Patent Description:
In general, LED current sources used in LED gears can be DC/DC converters (half bridge LLC, buck, flyback, etc.) that operate at a certain working frequency usually in the range between <NUM> and <NUM>. However, although the LED output current is essentially a DC current, a certain AC ripple may remain. This ripple has different frequency parts: there is a low frequency ripple (mainly at <NUM>) as well as a high frequency ripple which has the current source operating frequency (<NUM> to <NUM>, depending on the design and the working point). In order to control the current source, a control loop can be implemented which measures the LED current and controls the switches of the current source (e.g., in a half bridge LLC topology, the frequency of the half bridge is varied) in order to reach the desired target output current.

Measuring of the LED current (or another quantity that represents the LED current) can be done by sampling it with an analog to digital converter (ADC). Samples are taken at a fixed sampling frequency. In some cases, this sampling frequency can be at about <NUM> (corresponding to <NUM> sampling period). As in these designs the maximum operating frequency is at about <NUM>, the sampling frequency is much higher than the working frequency.

However, the sampling frequency of the LED current according to the invention can be at lower frequencies between e.g. <NUM> and <NUM> kHzand thus in the range of a working frequency of the LED current sources, which can be in the range of <NUM> to <NUM>.

In particular, the potential problem of aliasing occurs if the working frequency (and correspondingly the ripple on the LED current representing signal which is sampled) is close to the sampling frequency.

In general, the sampling frequency should be much higher than the working frequency, at least factor of <NUM>, preferably a factor of <NUM>, and this is called oversampling. In this case, the sampled signal (discrete signal) does well represent the real signal (analog signal). If the sampling frequency is below the working frequency, so-called undersampling, a reconstruction of the measured signal is not possible.

This problem is not that critical in certain LED gears in which the signal which is sampled (sensed LED current) is essentially a DC voltage which has only a small AC part. Therefore, it might be negligible if the AC part is not measured correctly.

However, problems can occur at low dim levels where the LED current,and, therefore, the DC voltage that represents the LED current, which is sampled by the ADC converter, is very low. In this case, the AC part has more influence and measurement errors caused by undersampling and aliasing may lead to light flicker problems. Such a low frequent aliasing signal (e.g., <NUM> or below) can influence the LED current controller, since the controller will react to the signal,which is not really existing, and try to eliminate it. Therefore, flicker problems can occur.

An LED power supply comprising a PFC and a DC/DC converter is disclosed, for example, in <CIT>. Frequency sweeping for suppressing flicker is proposed in <CIT>.

Thus, it is an objective to provide an improved LED converter, which, in particular, avoids the above mentioned problem of flicker.

According to a first aspect, the invention relates to a LED converter, according to claim <NUM>.

The switching frequency of the DC/DC switched converter may be in the order of <NUM> to <NUM>. The sampling frequency may be in the range of <NUM> to <NUM>, preferably <NUM> to <NUM>.

The difference set by the converter may be between <NUM>% and <NUM>%, preferably <NUM>% and <NUM>% of the switching frequency.

The difference set by the converter may be between <NUM> and <NUM>, preferably between <NUM> and <NUM>.

Preferably the sampling frequency is higher than the switching frequency, but may be also be lower.

This provides the advantage that flicker problems of the LED load are avoided by better separating the switching and sampling frequencies.

In an embodiment, the output voltage of the PFC circuit is controlled by a PFC control unit such that the resulting switching frequency is higher than a second preset value or the switching frequency of the switched DC/DC converter is controlled to deviate from a frequency value of the sampling frequency of the means for sampling by a predetermined value.

This provides the advantage that flicker problems of the LED load are avoided.

In an embodiment, the output DC voltage of the PFC circuit is controlled by the PFC control unit such that an artificial ripple, e.g. a triangular ripple, is added to the output DC voltage.

This provides the advantage that flicker problems may be avoided by adapting a simple solution, such as an artificial ripple.

In an embodiment, the output DC voltage of the PFC circuit is controlled by the PFC control unit such that the output DC voltage of the PFC circuit is kept constant while the switching frequency of the DC/DC switched converter is modulated accordingly.

In an embodiment, the DC/DC converter is a half-bridge LLC, flyback or buck converter.

This provides the advantage that well known converter topologies can be used.

In an embodiment, the means for sampling comprises an analog-to-digital, ADC, converter.

This provides the advantage that a well-known converter topologies can be used.

In an embodiment, the LED converter comprises an electromagnetic interference, EMI, filter.

In an embodiment, the LED converter comprises an isolation stage.

In an embodiment, the LED converter comprises a rectifying and sensing unit on a secondary side of the isolation stage configured to rectify and sense a current supplied to the LED load.

According to a second aspect, the invention relates to a luminaire comprising the LED converter according to the first aspect or any one of the embodiments thereof.

According to a third aspect, the invention relates to a method for supplying an LED load, according to claim <NUM>.

Aspects of the present invention are described herein in the context of a LED converter.

Various aspects of a LED converter will be presented. However, as those skilled in the art will readily appreciate, these aspects may be extended to aspects of LED converters without departing from the invention.

The term "LED luminaire" shall mean a luminaire with a light source comprising one or more LEDs or OLEDs. LEDs are well-known in the art, and therefore, will only briefly be discussed to provide a complete description of the invention.

Now referring to <FIG>, a LED converter <NUM> is shown according to an embodiment.

The LED converter <NUM> comprises a PFC circuitry 101a DC/DC converter <NUM>, a feedback control unit <NUM> and a means for sampling <NUM>.

The LED converter <NUM> comprises an actively switched power factor correction, PFC, circuit <NUM> configured to output a DC voltage. This DC voltage is a DC supply voltage of the switched DC/DC converter <NUM>, which is configured to supply an LED load <NUM> with a feedback controlled output current.

Moreover, the LED converter <NUM> comprises a means for sampling <NUM> a value representing the output current with a sampling frequency and for supplying it to a feedback control unit <NUM> which is configured to issue a control signal for at least one switch of the switched DC/DC converter <NUM>. The PFC circuit <NUM> and the switched converter <NUM> are designed such that a difference between a switching frequency of the DC/DC switched converter <NUM> and the sampling frequency of the means for sampling <NUM> is higher than a first preset value.

This provides the advantage that flicker problems of the LED load <NUM> are avoided, because the switching frequency and the sampling frequency can be better separated.

In an embodiment, the output voltage of the PFC circuit <NUM> is controlled by a PFC control unit or microcontroller or ASIC such that the resulting switching frequency is higher than a second preset value or the switching frequency of the switched DC/DC converter <NUM> is controlled to deviate from a frequency value of the sampling frequency of the means for sampling <NUM> by a predetermined value.

Advantageously, the LED converter <NUM> mitigates aliasing problems (which cause light flicker) by either statically changing the current source working frequency or dynamically modulating the current source working frequency at low dim levels. This change of current source working frequency can be done, for example, by a modulation added on the bus voltage (Vbus) which is the input voltage for the LED current source stage (e.g., half bridge LLC). This is, mainly, done at low dim levels, because there the AC ripple on the bus voltage is usually very low and, so, an artificial ripple is added (modulated) in order to avoid static aliasing frequencies.

Without a ripple on the bus voltage, the working frequency of the current source would be constant, if a constant ambient temperature and LED voltage are assumed. For example, if the working frequency is at <NUM> and the sampling frequency at <NUM>, the <NUM> aliasing can occur. If a ripple is added to the bus voltage, the working frequency of the current source will vary (as a controller comprised in the LED converter <NUM> needs to modify it due to the varying bus voltage). In this case, no static <NUM> aliasing occurs which is shown to have positive influence on the light flicker behavior.

Another possibility is to change the current source working frequency statically. In this case, the bus voltage is either increased or decreased (e.g., from the usually used <NUM> V to <NUM> V) in order to change the current source working frequency. Also, in this case, no low frequent aliasing occurs which is shown to have positive influence on the light flicker behavior.

The working frequency is, usually, known very accurately (low tolerance influences). The sampling frequency is known very accurate as well, because it is fixed in the ASIC design. Therefore, the controller or microcontroller could be configured to calculate the difference between current source working frequency and ADC sampling frequency, and interfere by adding a Vbus modulation, changing the Vbus level, or another means that changes the current source working frequency, if the difference gets too low and, therefore, potential flicker problems might arise.

<FIG> shows a schematic representation of the LED converter <NUM> according to an embodiment.

In particular, <FIG> shows a commonly used half bridge LLC circuit as DC/DC converter <NUM>. The power components as well as components used for output current sensing are shown. The power circuitry comprises the half bridge FETs M40 and M41, LLC resonance tank consisting of resonance capacitor C51 and resonance inductance which is the leakage inductance of L51, LLC transformer with primary winding L51d and secondary windings L51a and L51b, secondary side rectifier diodes D52a and D52b and output filter capacitor C52.

The output current sensing circuitry <NUM>, comprised in the means for sampling <NUM>,comprises current sensing transformer L52, with windings L52c and L52b in the power path (sensing the output current which splits through D52a and D52b) and winding L52a in the sensing path, rectifier FETs Q50 to Q53, buffer capacitor C30, shunt resistor R33 and (in this embodiment differential) RC filter consisting of R37, R38 and C28. The sensed and filtered (averaged) voltage between ISNSP and ISNSN, then, is amplified and sampled by an ADC converter <NUM> comprised in the means for sampling <NUM>.

<FIG> shows the corresponding waveforms of the LED converter <NUM> shown in <FIG>.

From top to bottom, in the first subplot, the gate signals of the two half bridge FETs M40 and M41 are shown.

In the second subplot, the half bridge middle point voltage is shown.

The third subplot shows the LLC primary side current, so the current flowing from the half bridge middle point into the resonance capacitor C51.

The fourth subplot shows the secondary side currents through the rectifier diodes D52a and D52b.

Finally, the last subplot shows the sensed and rectified output current (current through D52a and D52b, sensed with current transformer L52 and rectified) as well as its filtered version (ISNS) which is fed to the controller or ASIC.

In this example, the currents through the rectifier diodes D52a and D52b have different amplitudes. This is caused by different inductive couplings from LLC transformer primary winding L51d to the two secondary windings L51a and L51b. If the coupling from the primary winding to both secondary windings was the same, then, the current amplitudes would be the same. In reality, a small difference in amplitudes may occur as the two couplings will not match perfectly. Therefore, when observing the filtered signal ISNS, it can be seen that, essentially, two frequencies are present: the half bridge frequency (or period T_HB) and the double half bridge frequency (or the half period T_HB / <NUM>).

The mentioned aliasing problem occurs if the sampling frequency of the ADC <NUM> is very close to either the half bridge frequency or the double half bridge frequency.

In this example, a sinusoidal signal <NUM> with a certain frequency f_signal is sampled with a sampling frequency f_sampling (indicated by the sample numbers on the x-axis, as well as by the black dots) which is only slightly above the signal frequency. When the individual sample points are connected (reconstruction of a sinusoidal signal <NUM>), the signal <NUM> is shows up which has a very low frequency compared to the actual signal frequency f_signal. It has the frequency f_aliasing = f_sampling - f_signal. It can be seen that, if the sampling frequency was much larger than the signal frequency (e.g., f_sampling = <NUM>*f_signal, so <NUM> black dots will appear on the signal <NUM> during one period), the line <NUM> (measured and reconstructed signal) and the signal <NUM> would match.

For the LED gear problem this means the following. Assuming that the signal <NUM> has a very low frequent ripple on the ISNS signal (not the half bridge period or half of it, but for example <NUM> or so). In this case, with a sampling rate of about <NUM>, many sampling points during one (<NUM>) period of the low frequent ripple are available. This means that the LED current controller can easily compensate this low frequent ripple (as the ripple can be measured perfectly with the high sampling rate of <NUM>). In case this mentioned ripple on the ISNS signal has a higher frequency, for example in the range of the sampling rate, then the same problem as indicated in <FIG> will occur. The LED current controller is run with every new ADC sample. That means that the LED current controller will see that the measurement value (black dots, line <NUM> in <FIG>) changes with a low frequency (f_aliasing = f_sampling - f_ripple_on_isns) and, if this low frequency is low enough, that the controller can compensate it. The LED current controller will react and try to compensate the low frequent ripple (which is not really existing but just an artefact which occurs due to the mismatch of sampling and signal ripple frequency). When the difference between the sampling frequency and the frequency of the ripple on the ISNS signal gets above e.g. <NUM>, the reaction of the LED current controller (e.g., PI controller) will be low as the controller is optimized for slower fluctuations. Therefore, the worst case for this problem is when the aliasing frequency f_aliasing = f_sampling - f_ripple_on_isns is very low, for example, when the ripple frequency is slightly above or below the sampling frequency (e.g., only <NUM> difference).

The above mentioned problems can be avoided, as elucidated in the following. By varying the bus voltage, either statically (set the nominal voltage level from e.g. <NUM> VDC to a higher or lower level) or dynamically (add an artificial ripple to the <NUM> VDC bus voltage) the half bridge frequency, and, therefore, the ripple on the ISNS signal, changes and correspondingly the difference between the sampling frequency and this ripple frequency changes. This change needs to be done in such a way that this mentioned aliasing frequency f_aliasing increases so that the LED current controller will not react to it.

In some embodiments, the ADC sampling frequency is rather low at about <NUM>. Usually, the sampling frequency should be at least a factor of <NUM> higher than the highest frequency present in the measurement signal (which in our case is a signal that represents the LED current). The sampling frequency of about <NUM> is in the middle of the DC/DC converter working frequency range (which is approximately between <NUM> and <NUM>). The signal that represents the LED current is sampled by the ADC <NUM>. This signal is more or less a DC voltage. Nevertheless, it contains an AC ripple part which has the working frequency of the DC/DC converter <NUM>. A problem occurs if the working frequency is, e.g., at <NUM> (or, in general, very close to the ADC sampling frequency of <NUM>). The system (namely the control loop of the DC/DC converter <NUM>, consisting of the ADC <NUM> and the PI controller) in this case assumes that the LED current contains a <NUM> ripple (= <NUM> - <NUM>) which it tries to compensate.

The problem is that this <NUM> ripple is just an artefact that occurs due the performed undersampling. If the controller tries to compensate the not existing <NUM> ripple, then a light flicker occurs. If the working frequency is further away from the ADC sampling frequency, e.g. more than <NUM>, this problem is less critical because, e.g. at <NUM> frequency difference, the not existing ripple has a frequency of <NUM> which cannot be compensated by the rather slow PI controller.

In general, such working points (of the DC/DC converter <NUM>) should be avoided in which the working frequency is very close to the ADC sampling frequency (e.g., the two frequencies should not be closer to each other than <NUM>) and the LED current is low, because at low LED currently light flicker is more likely to be visible. Therefore, the goal is to detect such critical working points (preferably in an automated way directly by the microcontroller within the LED gear) and, then, to modify the whole system comprising the AC/DC converter and DC/DC converter <NUM> in order to avoid the critical working point. The modification aims to change the working frequency of the DC/DC converter <NUM> to bring the working frequency with some reserve e.g. <NUM> above or below the ADC sampling frequency. In the simplest way, this can be achieved by changing the input voltage of the DC/DC converter <NUM>. In our case, this is the bus voltage provided by the AC/DC (PFC) stage <NUM>.

Therefore, if the DC/DC converter <NUM> ends up in such a critical working point (determined by the LED current and LED voltage), the bus voltage can be increased (or decreased) either statically (e.g., from <NUM> V average value to <NUM> V), or an artificial ripple is added to the bus voltage (similar to the already known DC sweep) so that the DC/DC working frequency is not permanently very close to the ADC sampling frequency. So in a preferred embodiment, the DC/DC working frequency is indirectly modified by changing the output of the AC/DC (PFC) stage <NUM> whenever a critical DC/DC working frequency (which is too close to the ADC sampling frequency) would occur. If the DC/DC working frequency is directly modulated, at constant bus voltage, the ripple on the LED current would be increased.

<FIG> shows a block diagram of an LED gear or LED converter <NUM> in which the invention can be applied.

The mains voltage (e.g. 230V/ <NUM>) can be rectified and filtered by the block "EMI filter" <NUM>. The block "Boost PFC" <NUM> provides a DC bus voltage of e.g. <NUM> V at its output (pVbus). The EMI filter <NUM> and boost PFC together form an AC/DC converter. The bus voltage supplies the DC/DC converter <NUM> which drives the LED load <NUM>. In this case, the DC/DC converter <NUM> is a half-bridge LLC topology, but also other topologies such as e.g. flyback or buck converter are possible.

In case of half-bridge LLC (HB-LLC), the secondary side voltage of the LLC transformer <NUM> can be rectified in unit <NUM> and the LED output current can be sensed with, e.g., a current sense transformer <NUM>. The obtained signal that represents the LED current can be fed to the ASIC <NUM> which contains the control loop for both the boost PFC <NUM> as well as the half-bridge LLC. A microcontroller <NUM> (uC block) can support several interfaces to the outside (e.g., DALI bus) and can configure the ASIC <NUM> depending on the desired LED current.

<FIG> shows the boost PFC control loop of the PFC circuit <NUM> according to an embodiment.

A target bus voltage can be set by the microcontroller <NUM> (e.g., <NUM> VDC). It is compared in unit <NUM> to the sensed bus voltage and fed to a Boost PFC Ctrl block 101a. The sensing of the bus voltage pVbus is done, e.g., with an external voltage divider <NUM> and an ADC <NUM> within the ASIC <NUM>. The control loop in Boost PFC Ctrl unit 101a also obtains the boost PFC choke current zero cross (ZX) information. At its output, it delivers turn on times (ton) for the boost PFC switch. The block Boost PFC FET Drive 101b turns on/off the switch accordingly. The block Boost PFC 101c represents the actual boost PFC power circuit. Based on the working point (represented by the rectified mains input voltage as well as the load represented by the DC/DC converter stage <NUM>), different turn on / off times of the boost PFC switch are required. In general, the control loop aims to obtain fixed pVbus values such as e.g. <NUM> VDC in all working points.

<FIG> shows the control loop of the DC/DC stage (HB-LLC) <NUM> according to an embodiment.

A target LED current (Inom) can be set by the microcontroller <NUM>. It is compared in unit <NUM> to the measured LED current Imeas. The measurement of the LED current is, for example, done by a current transformer <NUM> (with some other components for rectification and filtering of the sensed signal) and an ADC <NUM>. In an embodiment, the LED current sensing unit <NUM> and the ADC converter <NUM> are comprised in the means for sampling <NUM>. The control error (err) is fed to a PI controller <NUM>. In an embodiment, the unit <NUM> and the PI controller <NUM> are comprised in the feedback control unit <NUM>.

The PI controller <NUM> delivers a half bridge period time at its output, wherein the half-bridge operates with a constant duty cycle of, e.g., <NUM>% and its frequency, or period, is varied. Based on this desired half-bridge period the block Half Bridge Drive 102a sets the turn on and off times of the two half bridge switches accordingly. Based on these turn on / off times and the input bus voltage pVbus, as well as based on the forward voltage of the connected LEDs (VLED), a certain LED current will flow. Which in turn is sensed and fed back to the control loop.

In an improved LED gear or LED converter <NUM> according to an embodiment, the scenario is as follows:.

When these two frequencies get too close to each other the microcontroller <NUM> can react in, e.g., three possible ways (three alternatives):.

In this case, the DC/DC converter working frequency will vary to compensate this ripple on pVbus. The DC/DC converter working frequency and the ADC sampling frequency will be separated most of the time (although they will be very close whenever the bus voltage is back at <NUM> V, but these are very short amounts of time). In such a way, the light flicker problem will likely not occur.

c) The bus voltage is not changed (boost PFC stage is not modified), but the working frequency of the DC/DC converter <NUM> is modulated. , a triangular ripple is added to this frequency. In this case, the ripple on the LED current will be increased but the light flicker problem will likely not occur as the DC/DC converter working frequency and the ADC sampling frequency will be separated wide enough most of the time.

From these three alternatives, only the second case b) falls under the scope of protection delimited by the independent claims. The other cases a) and c) present general background information.

<FIG> shows the relevant blocks of the overall control loop comprising the two above described control loops of a typical LED gear or LED converter <NUM> according to an embodiment.

The microcontroller <NUM> can provide several parameters to the ASIC <NUM>. Two of them are shown: the Vbus_target (the target value of the boost PFC output voltage) and Inom (the target LED current). Additionally, the microcontroller <NUM> reads several feedback parameters from the ASIC <NUM>. One of them is shown, namely tout_ctrl the target half bridge period time.

For example, the microcontroller <NUM> knows the ADC sampling frequency (or sampling period) of the ADC <NUM> utilized within the ASIC <NUM>. So, whenever the two periods (or frequencies) are too close to each other (e.g., closer than a certain limit), the microcontroller <NUM> will modify the system. Preferably, the steps a) or b) (as described in the scenario above) are done.

Utilizing step a), the microcontroller <NUM> can statically change Vbus_target from its previous value (e.g., <NUM> VDC which is the typical nominal value) to another value which can be higher or lower, e.g. <NUM> VDC. In this case, the AC/DC (boost PFC) control loop will control the boost PFC circuit in order to reach that target voltage. So pVbus will change from <NUM> V to <NUM> V. As pVbus is the input voltage to the HB-LLC stage, the LED current control loop will react in order to compensate the change in pVbus. That means that tout_ctrl will change to another value in order to reach the same LED current at changed pVbus.

Utilizing step b), the microcontroller <NUM> or PFC control unit can vary Vbus_target, e.g., in a triangular way, to introduce an artificial ripple on the nominal <NUM> V bus voltage, e. g between <NUM> V and <NUM> V. In this case, pVbus will vary and, therefore, also tout_ctrl should vary to compensate this ripple on pVbus. It is obvious that these things can also be done directly by the ASIC <NUM> if no microcontroller <NUM> is used within the system. Instead of varying Vbus_target, the ripple on the bus voltage can also be introduced by directly adding a triangular ripple onto the boost PFC FET turn ON time (ton).

Utilizing step c) the ASIC <NUM> can vary tout_ctrl directly in an, e.g., triangular (or sinusoidal, etc.) way. But as already mentioned with this approach (at constant pVbus) the ripple on ILED will be increased.

<FIG> shows a possible operation flow chart in case step a) is used according to an embodiment.

When the gear or LED converter <NUM> is turned on, or a new working point (e.g., target LED current or changed LED voltage) is set by the user in step <NUM>, first the nominal bus voltage is set in step <NUM>. After some stabilization time, (e.g., <NUM>), the resulting working period (or working frequency) of the DC/DC converter <NUM> is checked in step <NUM>.

If the absolute difference between the working frequency and the ADC sampling frequency is above a certain limit (e.g., <NUM>,kHz) as in step <NUM>, the operation is continued with these settings (nominal Vbus_target) in step <NUM>. If the difference is below said limit, Vbus_target as in step <NUM> is either increased or decreased statically. After some stabilization time (e.g., <NUM>) in step <NUM> again the resulting working period/frequency is checked. The modification is done as long as the two frequencies are separated wide enough. Then, the operation is continued as long as the working point is changed by the user (or the gear is turned off) in step <NUM>.

<FIG> shows a possible operation flow chart in case step b) is used according to an embodiment.

When the gear is turned on, or a new working point (e.g., target LED current or changed LED voltage) is set by the user in step <NUM>, first the nominal bus voltage is set in step <NUM>. Additionally, any ongoing bus voltage modulation is turned off in step <NUM>. After some stabilization time (e.g., <NUM>), the resulting working period (or working frequency) of the DC/DC converter <NUM> is checked in step <NUM>. If the absolute difference between the working frequency and the ADC sampling frequency is above a certain limit (e.g., <NUM>) in step <NUM>, then the operation is continued with these settings (nominal Vbus_target) in step <NUM>. If the difference is below said limit the modulation of the bus voltage is turned on in step <NUM>. The modulation is either done, e.g., by adding a ripple to Vbus_target (e.g., by the microcontroller <NUM>), or directly by the ASIC <NUM> by modulating the boost PFC turn ON time. Afterwards, the operation is continued in step <NUM> as long as the working point is changed by the user (or the gear is turned off) in step <NUM>.

<FIG> shows a possible operation flow chart in case step c) is used according to an embodiment.

When the gear is turned on, or a new working point (e.g. target LED current or changed LED voltage) is set by the user in step <NUM>, first the nominal bus voltage is set <NUM>. Additionally, any ongoing tout_ctrl modulation is turned off in step <NUM>. After some stabilization time (e.g., <NUM>), the resulting working period (or working frequency) of the DC/DC converter <NUM> is checked <NUM>. If the absolute difference between the working frequency and the ADC sampling frequency is above a certain limit (e.g., <NUM>) in step <NUM>, the operation is continued with these settings (nominal Vbus_target) in step <NUM>. If the difference is below said limit, the modulation of the DC/DC converter working period/frequency is turned on in step <NUM>. The modulation is done by adding a ripple (a sweep) to tout_ctrl, directly by the ASIC <NUM>. Afterwards, the operation is continued in step <NUM> as long as the working point is changed by the user (or the gear is turned off) in step <NUM>.

<FIG> shows a schematic flowchart of a method <NUM> for supplying an LED load according to an embodiment.

The method <NUM> comprises the following steps.

Claim 1:
LED converter (<NUM>), comprising:
- an actively switched power factor correction, PFC, circuit (<NUM>) outputting a DC voltage which is basis for a DC supply voltage of a switched DC/DC converter (<NUM>) of the LED converter (<NUM>), configured to supply an LED load (<NUM>) with a feedback-controlled output current said DC/DC converter (<NUM>) being configured to operate with frequency control, and a controller (<NUM>, <NUM>),
characterized by
- means for sampling (<NUM>) configured to sample a value representing the output current with a sampling frequency, and to supply it to a feedback control unit (<NUM>) of the LED converter (<NUM>) which is configured to issue a control signal for at least one switch of the switched DC/DC converter (<NUM>), wherein the PFC circuit (<NUM>) and the switched DC/DC converter (<NUM>) are designed such that a difference between a switching frequency of the DC/DC switched converter (<NUM>) and the sampling frequency of the means for sampling (<NUM>) is higher than a first preset value,
wherein the controller (<NUM>, <NUM>) is configured to control the output DC voltage of the PFC circuit (<NUM>) such that an artificial ripple, e.g. a triangular ripple, is dynamically added to the output DC voltage providing a varying output DC voltage, and the controller (<NUM>, <NUM>) is further configured to indirectly modify the switching frequency due to the varying output DC voltage, such that the switching frequency of said DC/DC converter (<NUM>) is varied.