Patent Description:
An electronic device such as a smartphone or a tablet personal computer (PC) may operate using power provided from a battery. A power management module (e.g., a power management integrated circuit (IC) (PMIC)) may transfer power provided from the battery to various components (e.g., a processor, a memory, or a communication chip) inside the electronic device.

The battery inside the electronic device may be charged through an external power source. Recently, various charging methods, wired or wireless, have been applied for fast charging. Among fast charging methods, a direct charging technology may allow an external power supply device (e.g., a power adapter) to control a constant voltage or a constant current for the battery inside the electronic device, and may simplify a charging circuit inside the electronic device. In addition, the direct charging technology may charge the battery with a high current while minimizing heat generation in the electronic device.

The following publications are related to the electronic device including a resonant charging circuit:.

A conventional electronic device may support charging by the direct charging technology using a switched capacitor voltage divider (SCVD) circuit. Unlike general switching converters, the SCVD circuit may achieve high efficiency of about <NUM>% or more to reduce heat generation of the electronic device, but may have a fixed voltage conversion ratio depending on the circuit configuration. Accordingly, a compatibility with various types of power devices or charging devices may be limited.

For example, when the SCVD circuit is connected to a legacy power adapter that supplies a fixed voltage of about <NUM> V or <NUM> V, because the SCVD circuit cannot perform the charging operation, a separate switching charger may have to be installed. As a result, a space for mounting components inside the electronic device may be reduced, and a cost of the electronic device may increase due to additional components.

In addition, to cope with both a wired power supply device and a wireless power supply device, a plurality of SCVD circuits and a plurality of switching chargers have to be installed, which further reduces the space for mounting components inside the electronic device.

In accordance with an aspect of the present disclosure, an electronic device is provided as per the appended claims.

An electronic device may use a plurality of resonant SCVDs to cope with all wireless/wired power supply devices that support the direct charging or do not support the direct charging.

An electronic device may configure a resonance type SCVD by using a flying capacitor having a relatively small capacity.

An electronic device may configure a <NUM>-level buck circuit by using a resonant SCVD circuit.

An electronic device may control a switching by using current flowing through the inductor of a resonant SCVD or voltage across both ends of the flying capacitor. Through this, power conversion efficiency during charging may be increased, and EMI may be reduced and system efficiency may be improved due to an operation of a resonant converter. In addition, the electronic device may improve efficiency under a light load by automatically reducing a switching frequency depending on a load fluctuation.

Hereinafter, various embodiments of the disclosure may be described with reference to accompanying drawings. Accordingly, those of ordinary skill in the art will recognize that modification, equivalent, and/or alternative on the various embodiments described herein can be variously made without departing from the scope of the disclosure. With regard to description of drawings, similar components may be marked by similar reference numerals.

<FIG> is a block diagram of an electronic device <NUM> in a network environment <NUM> according to various embodiments. An electronic device according to various embodiments of the present disclosure may include at least one of a smartphone, a tablet PC, a mobile phone, a video telephone, an electronic book reader, a desktop PC, a laptop PC, a netbook computer, a workstation, a server, personal digital assistant (PDA), a portable multimedia player (PMP), a Motion Picture Experts Group (MPEG-<NUM> or MPEG-<NUM>) Audio Layer <NUM> (MP3) player, a mobile medical device, a camera, or a wearable device. According to various embodiments, a wearable device may include at least one of an accessory type of device (e.g., a timepiece, a ring, a bracelet, an anklet, a necklace, glasses, a contact lens, or a head-mounted device (HMD)), a one-piece fabric or clothes type of device (e.g., electronic clothes), a body-attached type of device (e.g., a skin pad or a tattoo), or a bio-implantable type of device (e.g., implantable circuit). According to various embodiments, the electronic device may include at least one of, for example, televisions (TVs), digital versatile disk (DVD) players, audios, audio accessory devices (e.g., speakers, headphones, or headsets), refrigerators, air conditioners, cleaners, ovens, microwave ovens, washing machines, air cleaners, set-top boxes, home automation control panels, security control panels, game consoles, electronic dictionaries, electronic keys, camcorders, or electronic picture frames.

In another embodiment, the electronic device may include at least one of navigation devices, satellite navigation system (e.g., Global Navigation Satellite System (GNSS)), event data recorders (EDRs) (e.g., black box for a car, a ship, or a plane), vehicle infotainment devices (e.g., head-up display for vehicle), industrial or home robots, drones, automatic teller's machines (ATMs), points of sales (POSs), measuring instruments (e.g., water meters, electricity meters, or gas meters), or internet of things (e.g., light bulbs, sprinkler devices, fire alarms, thermostats, or street lamps). The electronic device according to an embodiment of this disclosure may not be limited to the above-described devices, and may provide functions of a plurality of devices like smartphones which has measurement function of personal biometric information (e.g., heart rate or blood glucose). In this disclosure, the term "user" may refer to a person who uses an electronic device or may refer to a device (e.g., an artificial intelligence electronic device) that uses the electronic device.

The electronic device <NUM> may communicate with an electronic device <NUM> through a first network <NUM> (e.g., a short-range wireless communication network) or may communicate with an electronic device <NUM> or a server <NUM> through a second network <NUM> (e.g., a long-distance wireless communication network) in a network environment <NUM>. According to an embodiment, the electronic device <NUM> may communicate with the electronic device <NUM> through the server <NUM>. According to an embodiment, the electronic device <NUM> may include a processor <NUM>, a memory <NUM>, an input device <NUM>, a sound output device <NUM>, a display device <NUM>, an audio module <NUM>, a sensor module <NUM>, an interface <NUM>, a haptic module <NUM>, a camera module <NUM>, a power management module <NUM>, a battery <NUM>, a communication module <NUM>, a subscriber identification module <NUM>, or an antenna module <NUM>. According to some embodiments, at least one (e.g., the display device <NUM> or the camera module <NUM>) among components of the electronic device <NUM> may be omitted or one or more other components may be added to the electronic device <NUM>. According to some embodiments, some of the above components may be implemented with one integrated circuit. For example, the sensor module <NUM> (e.g., a fingerprint sensor, an iris sensor, or an illuminance sensor) may be embedded in the display device <NUM> (e.g., a display).

The processor <NUM> may execute, for example, software (e.g., a program <NUM>) to control at least one of other components (e.g., a hardware or software component) of the electronic device <NUM> connected to the processor <NUM> and may process or compute a variety of data. According to an embodiment, as a part of data processing or operation, the processor <NUM> may load a command set or data, which is received from other components (e.g., the sensor module <NUM> or the communication module <NUM>), into a volatile memory <NUM>, may process the command or data loaded into the volatile memory <NUM>, and may store result data into a nonvolatile memory <NUM>. According to an embodiment, the processor <NUM> may include a main processor <NUM> (e.g., a central processing unit (CPU) or an application processor (AP)) and an auxiliary processor <NUM> (e.g., a graphic processing device, an image signal processor, a sensor hub processor, or a communication processor), which operates independently from the main processor <NUM> or with the main processor <NUM>. Additionally or alternatively, the auxiliary processor <NUM> may use less power than the main processor <NUM>, or is specified to a designated function. The auxiliary processor <NUM> may be implemented separately from the main processor <NUM> or as a part thereof.

The auxiliary processor <NUM> may control, for example, at least some of functions or states associated with at least one component (e.g., the display device <NUM>, the sensor module <NUM>, or the communication module <NUM>) among the components of the electronic device <NUM> instead of the main processor <NUM> while the main processor <NUM> is in an inactive (e.g., sleep) state or together with the main processor <NUM> while the main processor <NUM> is in an active (e.g., an application execution) state. According to an embodiment, the auxiliary processor <NUM> (e.g., the ISP or the CP) may be implemented as a part of another component (e.g., the camera module <NUM> or the communication module <NUM>) that is functionally related to the auxiliary processor <NUM>.

The memory <NUM> may store a variety of data used by at least one component (e.g., the processor <NUM> or the sensor module <NUM>) of the electronic device <NUM>. For example, data may include software (e.g., the program <NUM>) and input data or output data with respect to commands associated with the software. The memory <NUM> may include the volatile memory <NUM> or the nonvolatile memory <NUM>.

The program <NUM> may be stored in the memory <NUM> as software and may include, for example, a kernel <NUM>, a middleware <NUM>, or an application <NUM>.

The input device <NUM> may receive a command or data, which is used for a component (e.g., the processor <NUM>) of the electronic device <NUM>, from an outside (e.g., a user) of the electronic device <NUM>.

The sound output device <NUM> may output a sound signal to the outside of the electronic device <NUM>. The speaker may be used for general purposes, such as multimedia play or recordings play, and the receiver may be used for receiving calls. According to an embodiment, the receiver and the speaker may be either integrally or separately implemented.

The display device <NUM> may visually provide information to the outside (e.g., the user) of the electronic device <NUM>. For example, the display device <NUM> may include a display, a hologram device, or a projector and a control circuit for controlling a corresponding device. According to an embodiment, the display device <NUM> may include a touch circuitry configured to sense the touch or a sensor circuit (e.g., a pressure sensor) for measuring an intensity of pressure on the touch.

The audio module <NUM> may convert a sound and an electrical signal in dual directions. According to an embodiment, the audio module <NUM> may obtain the sound through the input device <NUM> or may output the sound through the sound output device <NUM> or an external electronic device (e.g., the electronic device <NUM> (e.g., a speaker or a headphone)) directly or wirelessly connected to the electronic device <NUM>.

The sensor module <NUM> may generate an electrical signal or a data value corresponding to an operating state (e.g., power or temperature) inside or an environmental state (e.g., a user state) outside the electronic device <NUM>. According to an embodiment, the sensor module <NUM> may include, for example, a gesture sensor, a gyro sensor, a barometric pressure sensor, a magnetic sensor, an acceleration sensor, a grip sensor, a proximity sensor, a color sensor, an infrared sensor, a biometric sensor, a temperature sensor, a humidity sensor, or an illuminance sensor.

The interface <NUM> may support one or more designated protocols to allow the electronic device <NUM> to connect directly or wirelessly to the external electronic device (e.g., the electronic device <NUM>). According to an embodiment, the interface <NUM> may include, for example, a high-definition multimedia interface (HDMI), a universal serial bus (USB) interface, a secure digital (SD) card interface, or an audio interface.

A connecting terminal <NUM> may include a connector that physically connects the electronic device <NUM> to the external electronic device (e.g., the electronic device <NUM>).

The haptic module <NUM> may convert an electrical signal to a mechanical stimulation (e.g., vibration or movement) or an electrical stimulation perceived by the user through tactile or kinesthetic sensations.

The camera module <NUM> may shoot a still image or a video image. According to an embodiment, the camera module <NUM> may include, for example, at least one or more lenses, image sensors, ISPs, or flashes.

According to an embodiment, the power management module <NUM> may be implemented as at least a part of a PMIC.

According to an embodiment, the battery <NUM> may include, for example, a non-rechargeable (primary) battery, a rechargeable (secondary) battery, or a fuel cell.

The communication module <NUM> may establish a direct (e.g., wired) or wireless communication channel between the electronic device <NUM> and the external electronic device (e.g., the electronic device <NUM>, the electronic device <NUM>, or the server <NUM>) and support communication execution through the established communication channel. The communication module <NUM> may include at least one CP operating independently from the processor <NUM> (e.g., the AP) and supporting the direct (e.g., wired) communication or the wireless communication. According to an embodiment, the communication module <NUM> may include a wireless communication module (or a wireless communication circuit) <NUM> (e.g., a cellular communication module, a short-range wireless communication module, or a global navigation satellite system (GNSS) communication module) or a wired communication module <NUM> (e.g., a local area network (LAN) communication module or a power line communication module). The corresponding communication module among the above communication modules may communicate with the external electronic device through the first network <NUM> (e.g., the short-range communication network such as a Bluetooth, a Wi-Fi direct, or an infrared data association (IrDA) or the second network <NUM> (e.g., the long-distance wireless communication network such as a cellular network, an internet, or a computer network (e.g., LAN or wide area network (WAN))). The above-mentioned various communication modules may be implemented into one component (e.g., a single chip) or into separate components (e.g., chips), respectively. The wireless communication module <NUM> may identify and authenticate the electronic device <NUM> using user information (e.g., international mobile subscriber identity (IMSI)) stored in the subscriber identification module <NUM> in the communication network, such as the first network <NUM> or the second network <NUM>.

The antenna module <NUM> may transmit or receive a signal or power to or from the outside (e.g., an external electronic device). According to an embodiment, the antenna module may include one antenna including a radiator made of a conductor or conductive pattern formed on a substrate (e.g., a PCB). In this case, for example, the communication module <NUM> may select one antenna suitable for a communication method used in the communication network such as the first network <NUM> or the second network <NUM> from the plurality of antennas. The signal or power may be transmitted or received between the communication module <NUM> and the external electronic device through the selected one antenna. According to some embodiments, in addition to the radiator, other parts (e.g., a RFIC) may be further formed as a portion of the antenna module <NUM>.

At least some components among the components may be connected to each other through a communication method (e.g., a bus, a general purpose input and output (GPIO), a serial peripheral interface (SPI), or a mobile industry processor interface(MIPI)) used between peripheral devices to exchange signals (e.g., a command or data) with each other.

According to an embodiment, the command or data may be transmitted or received between the electronic device <NUM> and the external electronic device <NUM> through the server <NUM> connected to the second network <NUM>. Each of the electronic devices 101a and 101b may be the same or different types as or from the electronic device <NUM>. According to an embodiment, all or some of the operations performed by the electronic device <NUM> may be performed by one or more external electronic devices among the external electronic devices 101a, 101b, or <NUM>. For example, when the electronic device <NUM> performs some functions or services automatically or by request from a user or another device, the electronic device <NUM> may request one or more external electronic devices to perform at least some of the functions related to the functions or services, in addition to or instead of performing the functions or services by itself. The one or more external electronic devices receiving the request may carry out at least a part of the requested function or service or the additional function or service associated with the request and transmit the execution result to the electronic device <NUM>. The electronic device <NUM> may provide the result as is or after additional processing as at least a part of the response to the request. To this end, for example, a cloud computing, distributed computing, or client-server computing technology may be used.

<FIG> is a block diagram illustrating a power management module and a battery, according to an embodiment.

Referring to <FIG>, an electronic device <NUM> may include a power management module <NUM> and a battery <NUM>. The power management module <NUM> (e.g., a charger IC or a PMIC) may include a power path distributor <NUM>, a first charging circuit <NUM>, and/or a second charging circuit <NUM>, and may control a flow of current output from the battery <NUM> and/or current flowing into the battery <NUM>.

The power management module <NUM> may utilize power received from the battery <NUM> as a system supply source. The power management module <NUM> may supply power suitable for a voltage level that is required for each element inside the electronic device <NUM>.

The power management module <NUM> may charge the battery <NUM> with power provided from a first external power supply device <NUM> or a second external power supply device <NUM>. The first external power supply device <NUM> may be a fast charging power adapter, a travel adapter (TA), or a battery pack. The second external power supply device <NUM> may be a wireless power transmission device (e.g., a transmitter of a wireless charging system).

The power management module <NUM> may further include a separate operation element (or a controller) therein. An operation element (e.g., a logic circuit or a micro controller unit (MCU)) inside the power management module <NUM> may perform calculations and controls related to charging or discharging the battery <NUM>. The operation element may control switches in the power path distributor <NUM>, the first charging circuit <NUM>, or the second charging circuit <NUM>. The operation element may control switches in the power path distributor <NUM>, the first charging circuit <NUM>, or the second charging circuit <NUM> in response to a control signal provided by a processor inside the electronic device <NUM>.

The power path distributor <NUM> may distribute power provided from the first external power supply device <NUM> or the second external power supply device <NUM> to the first charging circuit <NUM> and the second charging circuit <NUM>. The first charging circuit <NUM> and the second charging circuit <NUM> may charge the battery <NUM> using the power provided through the power path distributor <NUM>.

The first charging circuit <NUM> may include a first switch group <NUM>, a first flying capacitor <NUM>, and a first inductor <NUM>. The first charging circuit <NUM> may operate as a voltage dividing circuit due to a resonance of the first flying capacitor <NUM> and the first inductor <NUM>.

The second charging circuit <NUM> may include a second switch group <NUM>, a second flying capacitor <NUM>, and a second inductor <NUM>. The second charging circuit <NUM> may operate as the voltage dividing circuit due to the resonance of the second flying capacitor <NUM> and the second inductor <NUM>.

The power path distributor <NUM> may include a plurality of power distribution switches. The power path distributor <NUM> may control the plurality of power distribution switches such that the first charging circuit <NUM> and the second charging circuit <NUM> may operate in different modes. When the first charging circuit <NUM> operates in a mode in which the first flying capacitor <NUM> therein is discharged, the power path distributor <NUM> may allow the second charging circuit <NUM> to operate in a mode in which the second flying capacitor <NUM> is charged. When the first charging circuit <NUM> operates in a mode in which the first flying capacitor <NUM> is charged, the power path distributor <NUM> may allow the second charging circuit <NUM> to operate in a mode in which the second flying capacitor <NUM> is discharged (as shown in <FIG> and <FIG>).

The first charging circuit <NUM> and the second charging circuit <NUM> may operate in different modes depending on a connection state of the first external power supply device <NUM> and/or the second external power supply device <NUM>, or a type of the first external power supply device <NUM> and/or the second external power supply device <NUM>. When one of the first external power supply device <NUM> or the second external power supply device <NUM> supports a direct charging or a fast charging (e.g., a quick charge) among the fast charging methods, each of the first charging circuit <NUM> and the second charging circuit <NUM> may operate in a first mode having a fixed voltage conversion ratio (e.g., about <NUM>:<NUM>). The direct charging technology may be a charging method that allows the first external power supply device <NUM> (e.g., the power adapter) or the second external power supply device <NUM> to perform a constant voltage control or a constant current control for the battery <NUM> inside the electronic device <NUM>. The first external power supply device <NUM> may transmit and receive a signal related to charging of the battery <NUM> with the electronic device <NUM> through a power delivery (PD) communication. The first external power supply device <NUM> or the second external power supply device <NUM> may perform the constant voltage control and the constant current control for charging the battery <NUM> using a programmable power supply (PPS) function of a USB PD <NUM>. The second external power supply device <NUM> may be a wireless power transmission device, and a power supply part of the wireless power transmission device may transmit and receive a signal related to charging of the battery <NUM> with the electronic device <NUM> using an in-band communication (e.g., communication using a coil). The second external power supply device <NUM> may be connected to a TA for the fast charging, and a transmitter of the second external power supply device <NUM> may transmit and receive voltage information or current information regarding the direct charging with the electronic device <NUM> through the in-band communication (e.g., communication using the coil). The power supply part of the wireless power transmission device may perform the constant voltage control or the constant current control for charging the battery <NUM>.

When both the first external power supply device <NUM> and the second external power supply device <NUM> are connected, the power management module <NUM> may allow connection of one power supply device and may block the connection of another power supply device. The power management module <NUM> may allow the first charging circuit <NUM> or the second charging circuit <NUM> to operate in the first mode or the second mode depending on characteristics of the connected power supply device. The power management module <NUM> may select and connect a power supply device capable of the PD communication, or may select and connect the first external power supply device <NUM> that is connected by wire.

When the first external power supply device <NUM> or the second external power supply device <NUM> supports the direct charging, the constant voltage control or the constant current control inside the first external power supply device <NUM> or the second external power supply device <NUM> is performed, and each of the first charging circuit <NUM> and the second charging circuit <NUM> may charge the battery <NUM> by lowering a voltage, based on the fixed voltage conversion ratio (e.g., about <NUM>: <NUM>). In the first mode, the first charging circuit <NUM> and the second charging circuit <NUM> may operate with a relatively high charging efficiency (e.g., about <NUM>% or more), and then the heat generation of the first charging circuit <NUM> and the second charging circuit <NUM> may be reduced. In addition, in the first mode, each of the first charging circuit <NUM> and the second charging circuit <NUM> may have a switching signal having a sine wave characteristic, and then a switching loss may be reduced.

In the first mode, the first charging circuit <NUM> and the second charging circuit <NUM> may alternately operate in different sub-modes. In the first period, the first charging circuit <NUM> may operate in a sub-mode (hereinafter, referred to as a discharge mode) in which the first flying capacitor <NUM> therein is discharged, and the second charging circuit <NUM> may operate in a sub-mode (hereinafter, referred to as a charge mode) in which the second flying capacitor <NUM> therein is charged. In a second period consecutive to the first period, the first flying capacitor <NUM> inside the first charging circuit <NUM> may operate in the charge mode, and the second flying capacitor <NUM> inside the second charging circuit <NUM> may operate in the discharge mode (as shown in <FIG> and <FIG>).

When the first external power supply device <NUM> or the second external power supply device <NUM> is the legacy power adapter that does not support the direct charging, each of the first charging circuit <NUM> and the second charging circuit <NUM> may operate in the second mode in which a voltage conversion ratio is adjusted depending on a degree of charge of the battery <NUM>. In the second mode, each of the first charging circuit <NUM> and the second charging circuit <NUM> may operate as a <NUM>-level buck circuit in which the power conversion ratio is adjusted by a pulse width modulation (PWM) method. In the second mode, the first charging circuit <NUM> and the second charging circuit <NUM> may operate separately from each other depending on the degree of charge of the battery <NUM>.

In the second mode, a switching operation of the first switch group <NUM> of the first charging circuit <NUM> or the second switch group <NUM> of the second charging circuit <NUM> may be controlled based on the current flowing into the battery <NUM> or the voltage across both ends of the battery <NUM>. The first flying capacitor <NUM> of the first charging circuit <NUM> may operate in one of a charge state, an idle state, or a discharge state, based on the switching of the first switch group <NUM>. For another example, the second flying capacitor <NUM> of the second charging circuit <NUM> may operate in one of the charge state, the idle state, or the discharge state, based on a switching of the second switch group <NUM> (as shown in <FIG>).

The battery <NUM> may be charged with electric power provided from the first external power supply device <NUM> or the second external power supply device <NUM>. The battery <NUM> may supply power required for an operation of the electronic device <NUM>. The battery <NUM> may include, for example, a lithium-ion battery or a rechargeable battery.

<FIG> is a flowchart describing a charging method depending on a type of an external power supply device, according to an embodiment.

Referring to <FIG>, at step <NUM>, the power management module <NUM> of the electronic device <NUM> may identify a connection of an external power supply device (e.g., the first external power supply device <NUM> or the second external power supply device <NUM>). The power management module <NUM> may receive power from one of the first external power supply device <NUM> or the second external power supply device <NUM>.

When both the first external power supply device <NUM> and the second external power supply device <NUM> are connected, the power management module <NUM> may allow the connection of one power supply device and may block the connection of another power supply device. The power management module <NUM> may select and connect the power supply device capable of the PD communication, or may select and connect the first external power supply device <NUM> that is connected by wire.

At step <NUM>, the power management module <NUM> may determine whether the connected power supply device among the first external power supply device <NUM> or the second external power supply device <NUM> is a first type of the power supply device (e.g., the power adapter) in which the constant voltage control or the constant current control for charging the battery <NUM> is performed in the first external power supply device <NUM> or the second external power supply device <NUM>.

When the PD communication is possible with the connected power supply device (i.e., when the wireless power transmission device is connected, the power supply part of a wireless power supply device), the power management module <NUM> may determine that the connected power supply device is the first type of the power supply device. The power management module <NUM> may determine whether the connected power supply device is the first type of the power supply device by using the PPS function of the USB PD <NUM>.

When the first type of the first external power supply device <NUM> is connected, the first external power supply device <NUM> may directly perform the PD communication with the electronic device <NUM>. The second external power supply device <NUM> may be connected to the separate TA for fast charging, and the transmitter of the second external power supply device <NUM> may transmit and receive the voltage information or current information related to the direct charging with the electronic device <NUM> through the in-band communication (e.g., communication using the coil).

When the PD communication with the connected power supply device is not possible, the power management module <NUM> may determine that the connected power supply device is a second type of the power supply device (e.g., the legacy power adapter that does not support the direct charging). The second type of the first external power supply device <NUM> or the second external power supply device <NUM> may be a device that cannot perform the constant voltage control or the constant current control for the battery <NUM> inside the electronic device <NUM> and provides the fixed voltage. The second type of the power supply device may be the legacy power adapter or the wireless power transmission device (e.g., the transmitter of the wireless charging system) that supplies the fixed voltage of about <NUM> V or <NUM> V. The first charging circuit <NUM> or the second charging circuit <NUM> inside the electronic device <NUM> may change the voltage conversion ratio depending on the degree of charge of the battery <NUM>.

At step <NUM>, when the connected power supply device is the first type of the power supply device, the power management module <NUM> may allow each of the first charging circuit <NUM> and the second charging circuit <NUM> to operate in the first mode having the fixed voltage conversion ratio to perform the charging.

In the first mode, the voltage conversion ratio of each of the first charging circuit <NUM> and the second charging circuit <NUM> may be fixed to about <NUM>:<NUM>. When a maximum current capacity of a standard USB type C cable is 3A, the first type of the power supply device may supply power to the battery <NUM> while maintaining a maximum input current of about 3A or less. Each of the first charging circuit <NUM> and the second charging circuit <NUM> having the voltage conversion ratio of <NUM>:<NUM> drops the voltage of power transferred from the connected power supply device (e.g., the power adapter) by about <NUM>/<NUM> and may transfer the current increased by about <NUM> times to the battery <NUM>. Through this, while maintaining the maximum current capacity of the standard type C cable, it is possible to charge the battery <NUM> with a high power. In the first mode, the first charging circuit <NUM> and the second charging circuit <NUM> may obtain relatively high efficiency (e.g., about <NUM>% or more) and may perform the fast charging while reducing the heat generation.

In the first mode, the first charging circuit <NUM> and the second charging circuit <NUM> may alternately operate in different sub-modes. In the first cycle, the first flying capacitor <NUM> inside the first charging circuit <NUM> may operate in the discharge mode, and the second flying capacitor <NUM> inside the second charging circuit <NUM> may operate in the charge mode. In the second period consecutive to the first period, the first flying capacitor <NUM> inside the first charging circuit <NUM> may operate in the charge mode, and the second flying capacitor <NUM> inside the second charging circuit <NUM> may operate in the discharge mode.

In the first mode, the power management module <NUM> may control a switch included in the first charging circuit <NUM> and the second charging circuit <NUM>, based on a signal with a fixed first duty cycle (e.g., about <NUM>%) and a first frequency (e.g., about <NUM>). The first frequency may be set to the same value as a first resonant frequency of the first flying capacitor <NUM> and the first inductor <NUM>. Alternatively, the first frequency may be set to the same value as a second resonant frequency of the second flying capacitor <NUM> and the second inductor <NUM>. The first resonant frequency may be the same as the second resonant frequency.

The first charging circuit <NUM> may reduce a switching loss by a resonant operation of the first flying capacitor <NUM> and the first inductor <NUM>. In addition, the second charging circuit <NUM> may reduce the switching loss by the resonant operation of the second flying capacitor <NUM> and the second inductor <NUM> (as shown in <FIG>, <FIG>, <FIG>, or <FIG>).

At step <NUM>, when the connected first external power supply device <NUM> or the second external power supply device <NUM> is the second type of the power supply device (e.g., the legacy power adapter that does not support the direct charging), the power management module <NUM> may allow the first charging circuit <NUM> or the second charging circuit <NUM> to operate in the second mode in which the voltage conversion ratio is adjusted based on the charging ratio of the battery <NUM> and to perform the charging.

In the second mode, the power management module <NUM> may control a switch included in the first charging circuit <NUM> or the second charging circuit <NUM>, based on a signal having a second duty cycle and a second frequency, which are varied by the PWM method. The second frequency may be the same as or similar to the first frequency of the first mode.

<FIG> illustrates configurations of a power path distributor, a first charging circuit, and a second charging circuit, according to an embodiment. <FIG> is given as an example and is not limited thereto.

Referring to <FIG>, the power path distributor <NUM> may distribute power provided from the first external power supply device <NUM> or the second external power supply device <NUM> to the first charging circuit <NUM> and the second charging circuit <NUM>. When the first external power supply device <NUM> is connected to a connector (e.g., a USB port) 201a of the electronic device <NUM>, the power path distributor <NUM> may distribute power provided through a first power terminal 202a to the first charging circuit <NUM> and the second charging circuit <NUM>. When the second external power supply device <NUM> is connected to a wireless charging interface (e.g., a wireless charging coil and circuit) 201b of the electronic device <NUM>, the power path distributor <NUM> may distribute power provided through a second power terminal 203a to the first charging circuit <NUM> and the second charging circuit <NUM>.

The power path distributor <NUM> allows the first charging circuit <NUM> and the second charging circuit <NUM> to operate in different sub-modes through switching operation of first to sixth power distribution switches QVD1 to QVD6.

The power path distributor <NUM> may include the first to sixth power distribution switches QVD1 to QVD6 and a direct current (DC) blocking capacitor <NUM>. The first power distribution switch QVD1 and the third power distribution switch QVD3 may be connected in series between the first power terminal 202a and an input node 215a of the first charging circuit <NUM>. The second power distribution switch QVD2 may be connected between a first power node <NUM> of between the first power distribution switch QVD1 and the third power distribution switch QVD3 and a first ground terminal 202b. The fourth power distribution switch QVD4 and the sixth power distribution switch QVD6 may be connected in series between the second power terminal 203a and an input terminal 215b of the second charging circuit <NUM>. The fifth power distribution switch QVD5 may be connected between a second power node <NUM> of between the fourth power distribution switch QVD4 and the sixth power distribution switch QVD6 and a second ground terminal 203b. The DC blocking capacitor <NUM> may be connected between the first power node <NUM> and the second power node <NUM>.

The first charging circuit <NUM> may transfer power that is transferred from the first external power supply device <NUM> or the second external power supply device <NUM> to the battery <NUM>.

The first charging circuit <NUM> may be configured as a first resonant type SCVD circuit. The first charging circuit <NUM> may include first to fourth switches QHA1 to QHA4, the first flying capacitor <NUM>, and the first inductor <NUM>.

The first to fourth switches QHA1 to QHA4 may be sequentially connected between the input node 215a of the first charging circuit <NUM> and a ground (or a second pole (e.g., - terminal) of the battery <NUM>) <NUM>. The first switch QHA1 may be electrically connected between the input node 215a of the first charging circuit <NUM> and a first node <NUM> of the first charging circuit <NUM>. The second switch QHA2 may be electrically connected between the first node <NUM> and a second node <NUM> of the first charging circuit <NUM>. The third switch QHA3 may be electrically connected between the second node <NUM> and a third node <NUM>. The fourth switch QHA4 may be electrically connected between the third node <NUM> and the ground <NUM>.

The first to fourth switches QHA1 to QHA4 of the first charging circuit <NUM> may operate under control of a controller inside the power management module <NUM> or a processor inside the electronic device <NUM>.

The first flying capacitor <NUM> may be electrically connected between the first node <NUM> and the third node <NUM> of the first charging circuit <NUM>. The first inductor <NUM> may be electrically connected between the second node <NUM> of between the second switch QHA2 and the third switch QHA3 and a first pole (e.g., + pole) <NUM> of the battery <NUM>.

The first charging circuit <NUM> may operate in the first mode or the second mode depending on the type of the first external power supply device <NUM> or the second external power supply device <NUM>. The first mode may be a mode operating at the fixed voltage conversion ratio, and the second mode may be a mode operating at the voltage conversion ratio that is changed depending on the charging state of the battery <NUM>.

The second charging circuit <NUM> may transfer power transferred from the first external power supply device <NUM> or the second external power supply device <NUM> to the battery <NUM>.

The second charging circuit <NUM> may be configured as a second resonant type SCVD circuit. The second charging circuit <NUM> may include first to fourth switches QHB1 to QHB4, the second flying capacitor <NUM>, and the second inductor <NUM>.

The first to fourth switches QHB1 to QHB4 may be sequentially connected. The first switch QHB <NUM> may be electrically connected between the input terminal 215b of the second charging circuit <NUM> and a first node <NUM> of the second charging circuit <NUM>. The second switch QHB2 may be electrically connected between the first node <NUM> and a second node <NUM> of the second charging circuit <NUM>. The third switch QHB3 may be electrically connected between the second node <NUM> and a third node <NUM>. The fourth switch QHB4 may be electrically connected between the third node <NUM> and the ground <NUM>.

The first to fourth switches QHB1 to QHB4 of the second charging circuit <NUM> may operate under control of a controller inside the power management module <NUM> or a processor inside the electronic device <NUM>.

The second flying capacitor <NUM> may be electrically connected between the first node <NUM> and the third node <NUM> of the second charging circuit <NUM>. The second inductor <NUM> is electrically connected between the second node <NUM> between of the second switch QHB2 and the third switch QHB3 and the first pole (e.g., + pole) <NUM> of the battery <NUM>.

The second charging circuit <NUM> may operate in the first mode or the second mode depending on the type of the first external power supply device <NUM> or the second external power supply device <NUM>. The first mode may be a mode operating at the fixed voltage conversion ratio, and the second mode may be a mode operating at the voltage conversion ratio that is changed depending on the charging state of the battery <NUM>.

A DC bypass capacitor <NUM> may be disposed between both ends of the battery <NUM>. A control switch <NUM> for controlling charging may be added to the first pole (e.g., + pole) <NUM> of the battery <NUM>.

<FIG>, <FIG>, <FIG>, and <FIG> illustrate an operation in a first mode of a first charging circuit and a second charging circuit, according to an embodiment.

Referring to <FIG>, <FIG>, and <FIG>, when one of the first external power supply device <NUM> or the second external power supply device <NUM> is connected, the power path distributor <NUM> may transfer power provided from the connected power supply device to the first charging circuit <NUM> and the second charging circuit <NUM>.

When the first external power supply device <NUM> is connected and the second external power supply device <NUM> is not connected, the fourth power distribution switch QVD4 and the second power distribution switch QVD2 may maintain an OFF state. When the first external power supply device <NUM> is not connected and the second external power supply device <NUM> is connected, the first power distribution switch QVD1 and the fifth power distribution switch QVD5 may maintain the OFF state.

Hereinafter, a description will be given of a case in which the first external power supply device <NUM> is connected to the first charging circuit <NUM> and the second charging circuit <NUM>, but the disclosure is not limited thereto. In addition, hereinafter, a description will be given of a case in which each of the first charging circuit <NUM> and the second charging circuit <NUM> has a voltage conversion ratio of <NUM>:<NUM> (e.g., switching with a <NUM>% duty cycle), and an input voltage Vin of the first external power supply device <NUM> and a voltage Vo applied to the battery <NUM> have a ratio of <NUM>:<NUM>, but the disclosure is not limited thereto.

Referring to <FIG>, when the first external power supply device <NUM> that maintains <NUM> times 4Vo of the voltage Vo applied to the battery <NUM> is connected, and the second external power supply device <NUM> is not connected, the fourth power distribution switch QVD4 and the second power distribution switch QVD2 may maintain the OFF state. The DC blocking capacitor <NUM> of the power path distributor <NUM> may be maintained at twice 2Vo of the voltage Vo applied to the battery <NUM>.

When the connected first external power supply device <NUM> is of the first type, in a first period T1, the first power distribution switch QVD1 and the sixth power distribution switch QVD6 may be turned on. The first power terminal 202a and the input terminal 215b of the second charging circuit <NUM> may be conductive. Accordingly, twice 2Vo of the voltage Vo applied to the battery <NUM> may be applied to the input terminal 215b of the second charging circuit <NUM> by the DC blocking capacitor <NUM>.

Referring to <FIG>, in the first period T1, the first switch QHB1 and the third switch QHB3 may be turned on and the second switch QHB2 and the fourth switch QHB4 may be turned off among the first to fourth switches QHB1 to QHB4 of the second charging circuit <NUM>. Accordingly, the second flying capacitor <NUM> may be charged by resonance (charge mode).

In contrast, in the first period T1, the second switch QHA2 and the fourth switch QHA4 may be turned on and the first switch QHA1 and the third switch QHA3 may be turned off among the first to fourth switches QHA1 to QHA4 of the first charging circuit <NUM>. Accordingly, the first charging circuit <NUM> may charge the battery <NUM> by discharging the first flying capacitor <NUM> charged in a previous period of the first period T1 (discharge mode).

Referring to <FIG>, when the first external power supply device <NUM> is connected and the second external power supply device <NUM> is not connected, the fourth power distribution switch QVD4 and the second power distribution switch QVD2 may maintain the OFF state. The DC blocking capacitor <NUM> of the power path distributor <NUM> may be maintained at twice 2Vo of the voltage Vo applied to the battery <NUM>.

When the connected first external power supply device <NUM> is of the first type, in the second period T2, the fifth power distribution switch QVD5 and the third power distribution switch QVD3 may be turned on. The first ground terminal 202b of the first external power supply device <NUM> and the input node 215a of the first charging circuit <NUM> may be electrically connected to each other. Accordingly, twice 2Vo of the voltage Vo applied to the battery <NUM> may be applied to the input node 215a of the first charging circuit <NUM> by the DC blocking capacitor <NUM>.

Referring to <FIG>, in the second period T2, the first switch QHA1 and the third switch QHA3 may be turned on and the second switch QHA2 and the fourth switch QHA4 may be turned off among the first to fourth switches QHA1 to QHA4 of the first charging circuit <NUM>. Accordingly, the first flying capacitor <NUM> may be charged by resonance (charge mode).

In contrast, in the second period T2, the second switch QHB2 and the fourth switch QHB4 are turned on and the first switch QHB1 and the third switch QHB3 may be turned off among the first to fourth switches QHB1 to QHB4 of the second charging circuit <NUM>. Accordingly, the second charging circuit <NUM> may charge the battery <NUM> by discharging the second flying capacitor <NUM> charged in the first period T1 prior to the second period T2 (discharge mode).

Referring to <FIG>, in the first period T1, the first charging circuit <NUM> may charge the battery <NUM> by discharging the first flying capacitor <NUM> charged in the previous period of the first period T1 (discharge mode). The first flying capacitor <NUM> is discharged and may supply the current to the battery <NUM>. The first charging circuit <NUM> may charge the battery <NUM> by discharging the power of the first flying capacitor <NUM> through the first inductor <NUM>. A voltage Vcra across both ends of the first flying capacitor <NUM> may have a characteristic of a sine wave that gradually decreases.

In the first period T1, the second charging circuit <NUM> may charge the second flying capacitor <NUM> (charge mode). The second flying capacitor <NUM> is charged and may supply current to the battery <NUM>. The voltage Verb across both ends of the second flying capacitor <NUM> may have a characteristic of a sine wave that gradually increases.

In the second period T2, the second charging circuit <NUM> may charge the battery <NUM> by discharging the second flying capacitor <NUM> charged in the first period T1 (discharge mode). The second flying capacitor <NUM> is discharged and may supply current to the battery <NUM>. The second charging circuit <NUM> may charge the battery <NUM> by discharging the power of the second flying capacitor <NUM> through the second inductor <NUM>. The voltage Verb across the both ends of the second flying capacitor <NUM> may have the characteristic of the sine wave that gradually decreases.

In the second period T2, the first charging circuit <NUM> may charge the first flying capacitor <NUM> (charge mode). The first flying capacitor <NUM> is charged and may supply current to the battery <NUM>. The voltage Vcra across the both ends of the first flying capacitor <NUM> may have the characteristic of the sine wave that gradually increases.

<FIG> illustrates a switching control circuit of a voltage control method in a second mode, according to an embodiment. A charging circuit <NUM> in <FIG> may correspond to the first charging circuit <NUM> or the second charging circuit <NUM>, which operates in the second mode.

In <FIG>, when the first external power supply device <NUM>, which is the legacy power adapter that does not support the direct charging, is connected and the second external power supply device <NUM> is not connected, the first power distribution switch QVD1, the third power distribution switch QVD3, and the fifth power distribution switch QVD5 may maintain an ON state. The second power distribution switch QVD2, the fourth power distribution switch QVD4, and the sixth power distribution switch QVD6 may maintain the OFF state. Through this, the input voltage Vin applied to the first power terminal 202a may be applied to the input node 215a of the first charging circuit <NUM>. In this case, the charging circuit <NUM> may correspond to the first charging circuit <NUM> operating in the second mode.

In <FIG>, when the second external power supply device <NUM>, which is the wireless charging device that does not support the direct charging, is connected and the first external power supply device <NUM> is not connected, the second power distribution switch QVD2, the fourth power distribution switch QVD4, and the sixth power distribution switch QVD6 may maintain the ON state. The first power distribution switch QVD1, the third power distribution switch QVD3, and the fifth power distribution switch QVD5 may maintain the OFF state. Through this, the input voltage Vin applied to the second power terminal <NUM> a may be applied to the input terminal 215b of the second charging circuit <NUM>. In this case, the charging circuit <NUM> may correspond to the second charging circuit <NUM> operating in the second mode.

Referring to <FIG>, in the second mode, the voltage conversion ratio of the charging circuit <NUM> may be adjusted depending on the degree of charge of the battery <NUM>. In the second mode, the charging circuit <NUM> may operate as the <NUM>-level buck circuit in which the power conversion ratio is adjusted by the PWM method. In the second mode, the charging circuit <NUM> may operate depending on the degree of charge of the battery <NUM>.

In the second mode, a switching operation for a plurality of switches <NUM> to <NUM> of the charging circuit <NUM> (e.g., QHA1 to QHA4 or QHB1 to QHB4 in <FIG>) may be controlled based on the current flowing into the battery <NUM> or the voltage across the both ends of the battery <NUM>. A flying capacitor <NUM> (e.g., the first flying capacitor <NUM> or the second flying capacitor <NUM> of <FIG>) of the charging circuit <NUM> may operate in one of the charge state, the idle state, and the discharge state, based on the switching of the plurality of switches <NUM> to <NUM>.

The control circuit <NUM> in the power management module <NUM> may generate signals for controlling the first to fourth switches <NUM> to <NUM> of the charging circuit <NUM>.

In the first mode, the control circuit <NUM> may generate the first control signal G1 for controlling the first switch, the second control signal G2 for controlling the second switch, the third control signal G3 for controlling the third switch, and the fourth control signal G4 controlling the fourth switch <NUM>, based on a signal 801a of a clock generator CLK and an inverted signal 801b of the clock generator CLK.

In the first mode, the first control signal G1 may be the same as the third control signal G3, and the second control signal G2 may be the same as the fourth control signal G4. The second control signal G2 may have a phase opposite to that of the first control signal G1.

In the first mode, the first control signal G1 and the second control signal G2 may each have the fixed first duty cycle (e.g., about <NUM>%) and the first frequency (e.g., about <NUM>). The first frequency (e.g., about <NUM>) may be set to the same value as the resonant frequency of the flying capacitor <NUM> and the inductor <NUM> of the output terminal.

In the second mode, the control circuit <NUM> may determine the duty control voltage Vctrl, based on the voltage VBAT across the both ends of the battery <NUM> and the current IBAT flowing into the battery <NUM>.

The control circuit <NUM> may amplify a voltage difference between the voltage VBAT across the both ends of the battery <NUM> and the set reference voltage Vref through a first error amplifier <NUM>. The control circuit <NUM> may amplify a current difference between the current IBAT flowing into the battery <NUM> and the set reference current Iref through the second error amplifier <NUM>. The control circuit <NUM> may compare an output of the first error amplifier <NUM> with an output of the second error amplifier <NUM> through a comparator <NUM>, and may determine the duty control voltage Vctrl, based on a relatively small output value. In <FIG>, a case in which the duty control voltage Vctrl is determined by using both the voltage VBAT across the both ends of the battery <NUM> and the current IBAT flowing into the battery <NUM> is illustrated as an example, but the disclosure is not limited thereto. The duty control voltage Vctrl may be determined using one of the voltage VBAT across the both ends of the battery <NUM> and the current IBAT flowing into the battery <NUM>.

In the second mode, the control circuit <NUM> may generate the first to fourth control signals G1 to G4 using the duty control voltage Vctrl and the first triangle wave Vsaw1, or the duty control voltage Vctrl and the second triangle wave Vsaw2.

The control circuit <NUM> may generate a first control signal G1 for controlling the first switch <NUM> by comparing the duty control voltage Vctrl with the first triangle wave Vsaw1.

The control circuit <NUM> may change the first control signal G1 from a first state LOW to a second state HIGH in response to the clock signal CLK 801a. For example, the control circuit <NUM> may provide a toggling signal of the clock signal CLK to an S input 881a of a flip-flop <NUM>. The control circuit <NUM> may allow the first control signal G1 to maintain the second state HIGH when the duty control voltage Vctrl is greater than the first triangle wave Vsaw1.

The control circuit <NUM> may change the first control signal G1 from the second state HIGH to the first state LOW when the duty control voltage Vctrl is less than the first triangle wave Vsaw1. The control circuit <NUM> may provide a signal from an output terminal 851a of a coupler <NUM> that couples the duty control voltage Vctrl and the first triangle wave Vsaw1 to an R input 881b of the flip-flop <NUM>.

The control circuit <NUM> may generate the second control signal G2 for controlling the second switch <NUM> by comparing the duty control voltage Vctrl with the second triangle wave Vsaw2. The second triangle wave Vsaw2 may be a signal in which the first triangle wave Vsaw1 is shifted by half a period.

The control circuit <NUM> may change the second control signal G2 from the first state LOW to the second state HIGH in response to an inverted signal 801b of the clock signal CLK. The control circuit <NUM> may provide the inverted signal 801b of the clock signal CLK to an S input 882a of a flip-flop <NUM>. The control circuit <NUM> may allow the second control signal G2 to maintain the second state HIGH when the duty control voltage Vctrl is greater than the second triangle wave Vsaw2.

When the duty control voltage Vctrl is less than the second triangle wave Vsaw2, the control circuit <NUM> may change the second control signal G2 from the second state HIGH to the first state LOW. The control circuit <NUM> may provide a signal from an output terminal 852a of a coupler <NUM> that couples the duty control voltage Vctrl and the second triangle wave Vsaw2 to an R input 882b of the flip-flop <NUM>.

The control circuit <NUM> may generate the fourth control signal G4 by inverting a phase of the first control signal G1. The control circuit <NUM> may generate the third control signal G3 by inverting a phase of the second control signal G2.

<FIG> illustrates a control circuit that additionally uses a voltage across both ends of a flying capacitor, according to an embodiment.

Referring to <FIG>, the control circuit <NUM> may include a voltage detector <NUM>. The voltage detector <NUM> may have a simple circuit structure and thus may be easily implemented.

The voltage detector <NUM> may control the switching operation of the third switch <NUM> or the fourth switch <NUM> by using a voltage Vc across the both ends of the flying capacitor <NUM>. The voltage detector <NUM> may adjust a turn-on timing of the third switch <NUM> or a turn-on timing of the fourth switch <NUM>, depending on whether the voltage Vc across the both ends of the flying capacitor <NUM> is clamped to a ground voltage 0V or the input voltage VIN.

A turn-on time of the third switch <NUM> may be determined by a relatively faster one of a time point at which the voltage VCA of the first node <NUM> crosses to '<NUM>' (or a time point at which the voltage Vc across the both ends of the flying capacitor <NUM> is clamped to the ground voltage) and a time point at which the second switch <NUM> is turned off (e.g., a time point at which a signal is provided to the R input 882b of the flip-flop <NUM>) (as shown in <FIG>).

A turn-on time of the fourth switch <NUM> may be determined by a relatively faster one of a time point at which the voltage VCB of the third node <NUM> crosses to '<NUM>' (or a time point at which the voltage Vc across the both ends of the flying capacitor <NUM> is clamped to the input voltage VIN) and a time point at which the first switch <NUM> is turned off (e.g., a time point at which a signal is provided to the R input 881b of the flip-flop <NUM>) (as shown in <FIG>).

The voltage detector <NUM> may control the switching operation of the third switch <NUM> or the fourth switch <NUM> by using a time point at which when a current flowing through the inductor <NUM> (hereinafter, an inductor current IL) (or a sensing voltage Vcs proportional to the inductor current IL) becomes '<NUM>'.

A turn-off time of the third switch <NUM> may be determined by a relatively faster one of a time point at which the second switch <NUM> is turned on (e.g., a time point at which a signal is provided to the S input 882a of the flip-flop <NUM>) and a time point at which the inductor current IL becomes '<NUM>' (or a time point at which the sensing voltage Vcs crosses to '<NUM>') while the first switch <NUM> is conducting (turned on). Through this, it is possible to prevent the inductor current IL from falling below '<NUM>' (as shown in <FIG>).

A turn-off time of the fourth switch <NUM> may be determined by a relatively faster one of a time point at which the first switch <NUM> is turned on (e.g., a time point at which a signal is provided to the S input 881a of the flip-flop <NUM>) and a time point at which the inductor current IL becomes '<NUM>' (or a time point at which the sensing voltage Vcs crosses to '<NUM>') while the second switch <NUM> is conducting (turned on). Through this, it is possible to prevent the inductor current IL from falling below '<NUM>' (as shown in <FIG>).

<FIG> illustrates a change in a switching signal of a voltage control method in a first state of a second mode, according to an embodiment.

Referring to <FIG>, the first state may be a state in which the inductor current IL exceeds '<NUM>' and a clamping does not occur in the voltage across the both ends of the flying capacitor <NUM>.

The turn-on time and the turn-off time of the first switch <NUM> may be determined by the duty control voltage Vctrl and the first triangle wave Vsaw1. The first switch <NUM> may be turned on at a first time t1 when the first triangle wave Vsaw1 is less than the duty control voltage Vctrl. The second switch <NUM> may be in ON state at the first time <NUM>. The first switch <NUM> may be turned off at a fourth time t4 when the first triangle wave Vsaw1 becomes greater than the duty control voltage Vctrl. At the fourth time t4, the second switch <NUM> may be in ON state.

The turn-on time and the turn-off time of the second switch <NUM> may be determined by the duty control voltage Vctrl and the second triangle wave Vsaw2. The second triangle wave Vsaw2 may be a signal in which the first triangle wave Vsaw1 is shifted by a half period (e.g., a first half period T1-<NUM>). The second switch <NUM> may be turned off at a second time t2 when the second triangle wave Vsaw2 is greater than the duty control voltage Vctrl. At the second time t2, the first switch <NUM> may be in ON state. The second switch <NUM> may be turned on at a third time t3 when the second triangle wave Vsaw2 is less than the duty control voltage Vctrl. At the third time t3, the first switch <NUM> may be in ON state.

In the first half period T1-<NUM> of the first triangle wave Vsaw1, the first switch <NUM> is turned on (i.e., occurs at the first time <NUM>) and the second switch <NUM> is turned off (i.e., occurs at the second time t2). In the second half cycle T1-<NUM> of the first triangle wave Vsaw1, the second switch <NUM> is turned on (i.e., occurs at the third time t3), and the first switch <NUM> is turned off (i.e., occurs at the fourth time t4).

The control signal G3 of the third switch <NUM> may have a form opposite to the control signal G2 of the second switch <NUM>. The third switch <NUM> may be turned off when the second switch <NUM> is turned on, and may be turned on when the second switch <NUM> is turned off.

The control signal G4 of the fourth switch <NUM> may have a form opposite to the control signal G1 of the first switch <NUM>. The fourth switch <NUM> may be turned off when the first switch <NUM> is turned on, and may be turned on when the first switch <NUM> is turned off.

Turn-off timings of the third switch <NUM> and the fourth switch <NUM> may be changed to prevent the inductor current IL from falling below '<NUM>' (as shown in <FIG>). The turn-on timings of the third switch <NUM> and the fourth switch <NUM> may be changed by clamping of the flying capacitor <NUM> (as shown in <FIG>).

<FIG> illustrates a change in a switching signal of a voltage control method in a second state of a second mode, according to an embodiment.

Referring to <FIG>, the second state may be a state in which a zero current period of the inductor current IL (e.g., a period in which IL is '<NUM>') is included, and clamping does not occur in the voltage across the both ends of the flying capacitor <NUM>. The inductor current IL may be changed depending on a load (e.g., the battery <NUM>). When the load decreases, a discontinuous conduction mode (DCM) in which there is a period in which the inductor current IL becomes '<NUM>' may be operated (e.g., the second state). Since a period in which the current value of the inductor current IL becomes '<NUM>' is decreased as the load increases, a continuous conduction mode (CCM) in which the zero current period does not exist may be operated (the first state, refer to <FIG>).

In the second state, the switching operation of the first switch <NUM> and the second switch <NUM> may be the same as that of <FIG> associated with the first state.

In the second state, the turn-on time of the third switch <NUM> may be the same as the turn-off time of the second switch <NUM>, and the turn-on time of the fourth switch <NUM> may be the same as the turn-off time of the first switch <NUM>. The turn-on timing of the third switch <NUM> and the fourth switch <NUM> may be changed by clamping of the voltage across the both ends of the flying capacitor <NUM> (as shown in <FIG>).

The control circuit <NUM> may control the turn-off timing of the third switch <NUM> or the fourth switch <NUM> by using a time point at which the inductor current IL becomes '<NUM>'. In this case, the third switch <NUM> or the fourth switch <NUM> may operate as an ideal diode. Through this, it is possible to prevent the inductor current IL from becoming a negative value.

In the first half period T1-<NUM> of the first triangle wave Vsaw1, when the first switch <NUM> is in the turned on state at a fifth time t5 when the inductor current IL becomes '<NUM>', the third switch <NUM> may be turned off. Accordingly, the third switch <NUM> may be turned off before the second switch <NUM> is turned on.

When the second switch <NUM> is in the turned on state at a sixth time t6 when the inductor current IL becomes '<NUM>' in a second half period T1-<NUM> of the first triangle wave Vsaw1, the fourth switch <NUM> may be turned off. Accordingly, the fourth switch <NUM> may be turned off before the first switch <NUM> is turned on.

<FIG> illustrates a change in a switching signal of a voltage control method in a third state of a second mode, according to an embodiment.

Referring to <FIG>, the third state may be a state in which the voltage across the both ends of the flying capacitor <NUM> is clamped without including the zero current period of the inductor current IL (e.g., a period in which IL is '<NUM>').

In the third state, the switching operation of the first switch <NUM> and the second switch <NUM> may be the same as that of <FIG> associated with the first state.

The control circuit <NUM> may control the turn-on timing of the third switch <NUM> or the fourth switch <NUM> by using a time point at which the voltage Vc across the both ends of the flying capacitor <NUM> is clamped to the input voltage VIN or the ground voltage 0V. When the voltage across the both ends of the flying capacitor <NUM> is clamped to the input voltage VIN or the ground voltage 0V, if the third switch <NUM> and the fourth switch <NUM> are not turned on, and the current may flow through body diodes inside the third switch <NUM> and the fourth switch <NUM>, and switching loss may increase. When the voltage across the both ends of the flying capacitor <NUM> is clamped to the input voltage VIN or the ground voltage 0V, the control circuit <NUM> may reduce losses due to current flowing through the body diodes inside the third switch <NUM> and the fourth switch <NUM> by turning on the third switch <NUM> and the fourth switch <NUM>.

Since the voltage of the flying capacitor <NUM> is in a floating state, the control circuit <NUM> may detect a zero crossing point of the upper voltage VCA (e.g., the voltage of the first node <NUM>) of the flying capacitor <NUM> and a zero crossing point of the lower voltage VCB (e.g., the voltage of the third node <NUM>) without directly detecting the voltage Vc across both ends of the flying capacitor <NUM>, and may determine the turn-on time of the third switch <NUM> and the fourth switch <NUM>.

In the first half-period T1-<NUM> of the first triangle wave Vsaw1, the fourth switch <NUM> may be turned on at a seventh time t7 when the voltage VCB of the third node <NUM> crosses to '<NUM>' (e.g., the voltage Vc across both ends of flying capacitor <NUM> being clamped to the input voltage VIN). Accordingly, the fourth switch <NUM> may be turned on before the first switch <NUM> is turned off. The seventh time t7 may be a time point when the body diode inside the fourth switch <NUM> starts to conduct.

In the second half period T1-<NUM> of the first triangle wave Vsaw1, the third switch <NUM> may be turned on at an eighth time t8 when the voltage VCA of the first node <NUM> crosses to '<NUM>' (e.g., the voltage Vc across the both ends of the flying capacitor <NUM> being clamped to the ground voltage 0V). Accordingly, the third switch <NUM> may be turned on before the second switch <NUM> is turned off. The eighth time t8 may be a time point at which the body diode inside the third switch <NUM> starts to conduct.

The turn-off time of the third switch <NUM> may be the same as the turn-on time of the second switch <NUM>, and the turn-off time of the fourth switch <NUM> may be the same as the turn-on time of the first switch <NUM>.

<FIG> illustrates a change in a switching signal of a voltage control method in a fourth state of a second mode, according to an embodiment.

Referring to <FIG>, the fourth state may be a state in which the zero current period of the inductor current IL (e.g., a period in which IL is '<NUM>') is included, and the clamping occurs in the voltage across the both ends of the flying capacitor <NUM>.

In the fourth state, the switching operation of the first switch <NUM> and the second switch <NUM> may be the same as that of <FIG> associated with the first state.

A turn-on operation of the third switch <NUM> and the fourth switch <NUM> may be changed at a time point at which the voltage Vc of both ends of the flying capacitor <NUM> is clamped to the input voltage VIN or the ground voltage 0V. The turn-on operation of the third switch <NUM> and the fourth switch <NUM> may be the same as that of <FIG>, and a turn-off operation of the third switch <NUM> and the fourth switch <NUM> may be the same as that of <FIG>.

In the first half period T1-<NUM> of the first triangle wave Vsaw1, the fourth switch <NUM> may be turned on at the seventh time t7 when the voltage VCB of the third node <NUM> crosses to '<NUM>' (e.g., the voltage Vc across the both ends of the flying capacitor <NUM> being clamped to the input voltage VIN). The fourth switch <NUM> may be turned on before the first switch <NUM> is turned off.

In the first half period T1-<NUM> of the first triangle wave Vsaw1, when the first switch <NUM> is in the turned on state at the fifth time t5 when the inductor current IL becomes '<NUM>', the third switch <NUM> may be turned off. The third switch <NUM> may be turned off before the second switch <NUM> is turned on.

In the second half period T1-<NUM> of the first triangle wave Vsaw1, the third switch <NUM> may be turned on at the eighth time t8 when the voltage VCA of the first node <NUM> crosses to '<NUM>' (e.g., the voltage Vc of both ends of the flying capacitor <NUM> being clamped to the ground voltage 0V). The third switch <NUM> may be turned on before the second switch <NUM> is turned off.

In the second half period T1-<NUM> of the first triangle wave Vsaw1, when the second switch <NUM> is in the turned on state at the sixth time t6 when the inductor current IL is '<NUM>' (e.g., the sensing voltage Vcs is '<NUM>'), the fourth switch <NUM> may be turned off. The fourth switch <NUM> may be turned off before the first switch <NUM> is turned on.

<FIG> illustrates a switching control circuit of a current control method in a second mode, according to an embodiment. <FIG> is an example, and the disclosure is not limited thereto. The charging circuit <NUM> in <FIG> may correspond to the first charging circuit <NUM> or the second charging circuit <NUM> operating in the second mode.

Referring to <FIG>, in the second mode, the voltage conversion ratio of the charging circuit <NUM> may be adjusted based on the degree of charge of the battery <NUM>. In the second mode, the charging circuit <NUM> may operate as the <NUM>-level buck circuit in which the power conversion ratio is adjusted in the PWM method. In the second mode, the charging circuit <NUM> may operate depending on the degree of charge of the battery <NUM>.

In the second mode, the switching operation of the plurality of switches <NUM> to <NUM> (e.g., QHA1 to QHA4 or QHB1 to QHB4 in <FIG>) of the charging circuit <NUM> may be controlled based on the current flowing into the battery <NUM> or the voltage across the both ends of the battery <NUM>. The flying capacitor <NUM> (e.g., the first flying capacitor <NUM> or the second flying capacitor <NUM> in <FIG>) of the charging circuit <NUM> may operate in one of the charge state, the idle state, or the discharge state depending on the switching of the plurality of switches <NUM> to <NUM>.

A control circuit <NUM> may generate signals for controlling the first to fourth switches <NUM> to <NUM>.

In the first mode, the control circuit <NUM> may generate the first control signal G1 by using a signal of a first clock generator 1401a CLK1 having a <NUM>% duty cycle. The control circuit <NUM> may generate the second control signal G2 for controlling the second switch, based on a signal of a second clock generator 1401b CLK2 having a <NUM>% duty cycle. The signal of the second clock generator 1401b CLK2 may be a signal obtained by inverting the signal of the first clock generator 1401a CLK1.

In the first mode, the third control signal G3 may be the same as the first control signal G1. The fourth control signal G4 that controls the fourth switch <NUM> may be the same as the second control signal G2. The second control signal G2 may have a phase opposite to that of the first control signal G1.

The control circuit <NUM> may amplify a voltage difference between the voltage VBAT across the both ends of the battery <NUM> and the set reference voltage Vref through a first error amplifier <NUM>. The control circuit <NUM> may amplify a current difference between the current IBAT flowing into the battery <NUM> and the set reference current Iref through a second error amplifier <NUM>. The control circuit <NUM> may compare an output of the first error amplifier <NUM> with an output of the second error amplifier <NUM> through a comparator <NUM>, and may determine the duty control voltage Vctrl, based on a relatively smaller value. In <FIG>, a case in which the duty control voltage Vctrl is determined by using both the voltage VBAT across the both ends of the battery <NUM> and the current IBAT flowing into the battery <NUM> is illustrated, but the disclosure is not limited thereto. The duty control voltage Vctrl may be determined using one of the voltage VBAT across the both ends of the battery <NUM> and the current IBAT flowing into the battery <NUM>.

In the second mode, the control circuit <NUM> may control the first to fourth switches <NUM> to <NUM> in a current mode control method, based on the inductor current IL flowing through the inductor <NUM> included in the charging circuit <NUM>. The control circuit <NUM> may adjust the switching frequency of the first to fourth switches <NUM> to <NUM> by using the sensing voltage Vcs proportional to the detected inductor current IL. The current control method using the inductor current IL may enable more precise switching control than the voltage control method in <FIG>.

When using the inductor current IL in the second mode, the switching frequency of the first to fourth switches <NUM> to <NUM> may be the same as or similar to the switching frequency in the first mode. Accordingly, in the second mode of the current mode control method, a power conversion efficiency may be relatively high, and an electromagnetic interference (EMI) reduction and a system efficiency may be improved by the operation of the resonant converter. In addition, in the second mode of the current mode control method, the switching frequency is automatically reduced depending on load fluctuations, thereby improving efficiency under light load.

The control circuit <NUM> may apply a hysteresis voltage VH to the duty control voltage Vctrl. The control circuit <NUM> may input a first band voltage (hereinafter, a band upper limit voltage) (Vctrl+VH) that is generated by adding the hysteresis voltage VH <NUM> to the duty control voltage Vctrl to a first cross detector <NUM>. The control circuit <NUM> may input a second band voltage (hereinafter, a band lower limit voltage) (Vctrl-VH) that is generated by lowering the hysteresis voltage VH <NUM> from the duty control voltage Vctrl to a second cross detector <NUM>.

The control circuit <NUM> may change the hysteresis voltage VH to determine a switching frequency and a ripple of the inductor current IL. The control circuit <NUM> may change the hysteresis voltage VH (e.g., <NUM> and/or <NUM>) by using a phase-locked loop (PLL) circuit.

The control circuit <NUM> may generate the inductor sensing voltage Vcs generated based on the inductor current IL. The inductor current IL and the inductor sensing voltage Vcs may have a linear relationship (Vcs=k*IL). The inductor sensing voltage Vcs may be determined by a time point when a sensing signal of the inductor current IL reaches the band upper limit voltage and the band lower limit voltage, respectively.

The inductor sensing voltage Vcs may be input to the first cross detector <NUM> and the second cross detector <NUM>, respectively. The first cross detector <NUM> may generate a first trigger signal through an output terminal 1451a at a timing when the inductor sensing voltage Vcs and the band upper limit voltage Vctrl+VH are the same. The second cross detector <NUM> may generate a second trigger signal through an output terminal 1452a at a timing when the inductor sensing voltage Vcs and the band lower limit voltage Vctrl-VH are the same.

The control circuit <NUM> may turn on the first switch <NUM> and the second switch <NUM> at different timings, based on the second trigger signal. The first switch <NUM> may be turned on by the second trigger signal in the first period of the inductor sensing voltage Vcs, and the second switch <NUM> may be turned on by the second trigger signal in the second period (e.g., a subsequent period following the first period) of the inductor sensing voltage Vcs.

The control circuit <NUM> may turn off the first switch <NUM> and the second switch <NUM> at different timings, based on the first trigger signal. In the previous example, the first switch <NUM> may be turned off by the first trigger signal in the second period of the inductor sensing voltage Vcs, and the second switch <NUM> may be turned off by the first trigger signal in a third period (e.g., a subsequent period following the second period) of the inductor sensing voltage Vcs.

A first signal divider <NUM> may receive the first trigger signal through the output terminal 1451a of the first cross detector <NUM>. The first signal divider <NUM> may include a toggle flip-flop that operates by using the first trigger signal as a clock signal. A first output terminal 1471a of the first signal divider <NUM> may generate a signal for turning off the second switch <NUM>. The first output terminal 1471a may be connected to an R terminal of a set-reset (SR) flip-flop <NUM> that generates the second control signal G2. A second output terminal 1471b of the first signal divider <NUM> may generate a signal for turning off the first switch <NUM>. The second output terminal 1471b of the first signal divider <NUM> may be connected to the R terminal of an SR flip-flop <NUM> that generates the first control signal G1.

A second signal divider <NUM> may receive the second trigger signal through the output terminal 1452a of the second cross detector <NUM>. The second signal divider <NUM> may include a toggle flip-flop that operates by using the second trigger signal as a clock signal. A first output terminal 1472a of the second signal divider <NUM> may generate a signal for turning on the second switch <NUM>. The first output terminal 1472a may be connected to the S terminal of the SR flip-flop <NUM> that generates the second control signal G2. A second output terminal 1472b of the second signal divider <NUM> may generate a signal for turning on the first switch <NUM>. The second output terminal 1472b of the second signal divider <NUM> may be connected to the S terminal of the SR flip-flop <NUM> that generates the first control signal G1.

Referring to <FIG>, the control circuit <NUM> may further include a voltage detector <NUM>.

The voltage detector <NUM> may control a switching operation of the third switch <NUM> or the fourth switch <NUM> by using the voltage Vc across of the both ends of the flying capacitor <NUM>. In addition, the voltage detector <NUM> may control the switching operation of the third switch <NUM> or the fourth switch <NUM> by using a time point when the sensing voltage Vcs becomes '<NUM>'.

The voltage detector <NUM> may control the switching operation of the third switch <NUM> or the fourth switch <NUM> by using the voltage Vc across the both ends of the flying capacitor <NUM>. The voltage detector <NUM> may adjust the turn-on timing of the third switch <NUM> or the turn-on timing of the fourth switch <NUM> depending on whether the voltage Vc across the both ends of the flying capacitor <NUM> is clamped to the ground voltage 0V or the input voltage VIN.

The turn-on timing of the third switch <NUM> may be determined by a relatively faster one of a time point at which the voltage VCA of the first node <NUM> crosses to '<NUM>' (or a time point at which the voltage Vc across the both ends of the flying capacitor <NUM> is clamped to the ground voltage) and a point at which the second switch <NUM> is turned off (e.g., a time point at which a signal is provided to the first output terminal 1471a of the first signal divider <NUM>) (as shown in <FIG>).

The turn-on time of the fourth switch <NUM> may be determined by a relatively faster one of a time point at which the voltage VCB of the third node <NUM> crosses to '<NUM>' (or a time point at which the voltage Vc across the both ends of the flying capacitor <NUM> is clamped to the input voltage VIN) and a time point at which the first switch <NUM> is turned off (e.g., a time point at which a signal is provided to the second output terminal 1471b of the first signal divider <NUM>) (as shown in <FIG>).

The voltage detector <NUM> may control the switching operation of the third switch <NUM> or the fourth switch <NUM> by using a time point at which the inductor current IL flowing through the inductor <NUM> (or the sensing voltage Vcs proportional to the inductor current IL) becomes '<NUM>'.

The turn-off time of the third switch <NUM> may be determined by a relatively faster one of a time point at which the second switch <NUM> is turned on (e.g., a time point at which a signal is provided to the first output terminal 1472a of the second signal divider <NUM>) and a time point at which the inductor current IL crosses to '<NUM>' while the first switch <NUM> is conducting (i.e., turn-on) (e.g., a time point at which the sensing voltage Vcs crosses to '<NUM>'). Through this, it is possible to prevent the inductor current IL from falling below '<NUM>' (as shown in <FIG>).

The turn-off time of the fourth switch <NUM> may be determined by a relatively faster one of a time point at which the first switch <NUM> is turned on (e.g., a time point at which a signal is provided to the second output terminal 1472b of the second signal divider <NUM>) and a time point at which the inductor current IL crosses to '<NUM>' while the second switch <NUM> is conducting (turn-on) (e.g., a time point at which the sensing voltage Vcs crosses to '<NUM>'). Through this, it is possible to prevent the inductor current IL from falling below '<NUM>' (as shown in <FIG>).

<FIG> illustrates a change in a switching signal of a current control method in a first state of a second mode, according to an embodiment.

Referring to <FIG>, the first state may be a state in which the inductor current IL exceeds '<NUM>' and the clamping does not occur in the voltage across the both ends of the flying capacitor <NUM>.

The turn-on time of the first switch <NUM> and the turn-on time of the second switch <NUM> may be determined by the inductor sensing voltage Vcs and the band lower limit voltage Vctrl-VH. In the first period T1 of the sensing voltage Vcs, the first switch <NUM> may be turned on at a first time t1 when the inductor sensing voltage Vcs and the band lower limit voltage Vctrl-VH are the same. The second switch <NUM> may be in ON state at the first time <NUM>. In the second period T2 of the sensing voltage Vcs, the second switch <NUM> may be turned on at the third time t3 when the inductor sensing voltage Vcs and the band lower limit voltage Vctrl-VH are the same. At the third time t3, the first switch <NUM> may be in ON state.

The turn-off time of the first switch <NUM> and the turn-off time of the second switch <NUM> may be determined by the inductor sensing voltage Vcs and the band upper limit voltage Vctrl+VH. In the first period T1, the second switch <NUM> may be turned off at the second time t2 when the inductor sensing voltage Vcs and the band upper limit voltage Vctrl+VH are the same. At the second time t2, the first switch <NUM> may be in ON state. In the second period T2, the first switch <NUM> may be turned off at the fourth time t4 when the inductor sensing voltage Vcs and the band upper limit voltage Vctrl+VH are the same. At the fourth time t4, the second switch <NUM> may be ON state.

In the first period T1 and the second period T2, the turn-on of the first switch <NUM> (e.g., occurs at the first time <NUM>), the turn-off of the second switch <NUM> (e.g., occurs at the second time t2), the turn-on of the second switch <NUM> (e.g., occurs at the third time t3), and the turn-off of the first switch <NUM> (e.g., occurs at the fourth time t4) may occur sequentially.

The turn-off timing of the third switch <NUM> and the fourth switch <NUM> may be changed to prevent the inductor current IL from falling below '<NUM>' (as shown in <FIG>). The turn-on timing of the third switch <NUM> and the fourth switch <NUM> may be changed by clamping (as shown in <FIG>).

<FIG> illustrates a change in a switching signal of a current control method in a second state of a second mode, according to an embodiment.

Referring to <FIG>, the second state may be a state in which the zero current period of the inductor current IL (e.g., the period in which IL is '<NUM>') is included, and the clamping does not occur in the voltage across the both ends of the flying capacitor <NUM>. The inductor current IL may be changed depending on the load (e.g., the battery <NUM>). When the load decreases, the DCM in which there is a period in which the inductor current IL becomes '<NUM>' may be operated (e.g., the second state). Since a period in which the current value of the inductor current IL becomes '<NUM>' is decreased as the load increases, the CCM in which the zero current period does not exist may be operated (e.g., the first state, as shown in <FIG>).

The turn-on timing of the third switch <NUM> and the fourth switch <NUM> may be changed by clamping (as shown in <FIG>).

The control circuit <NUM> may control the turn-off timing of the third switch <NUM> or the fourth switch <NUM> by using a time point at which the inductor current IL becomes '<NUM>'. In this case, the third switch <NUM> or the fourth switch <NUM> may operate as the ideal diode. Through this, it is possible to prevent the inductor current IL from becoming a negative value.

In the first period T1, when the first switch <NUM> is in the turned on state at the fifth time t5 when the inductor current IL is '<NUM>' (e.g., the sensing voltage Vcs is '<NUM>'), the third switch <NUM> may be turned off. Accordingly, the third switch <NUM> may be turned off before the second switch <NUM> is turned on.

In the second period T2, when the second switch <NUM> is in the turned on state at the sixth time t6 when the inductor current IL is '<NUM>' (e.g., the sensing voltage Vcs is '<NUM>'), the fourth switch <NUM> may be turned off. Accordingly, the fourth switch <NUM> may be turned off before the first switch <NUM> is turned on.

<FIG> illustrates a change in a switching signal of a current control method in a third state of a second mode, according to an embodiment.

Referring to <FIG>, the third state may be a state in which the zero current period of the inductor current IL (e.g., a period in which IL is '<NUM>') is not included, and clamping occurs in the voltage across the both ends of the flying capacitor <NUM>.

The control circuit <NUM> may control the turn-on timing of the third switch <NUM> or the fourth switch <NUM> by using a time point at which the voltage across the both ends of the flying capacitor <NUM> is clamped to the input voltage VIN or the ground voltage 0V. When the voltage across the both ends of the flying capacitor <NUM> is clamped to the input voltage VIN or the ground voltage 0V, if the third switch <NUM> and the fourth switch <NUM> are not turned on, the current may flow through the body diodes inside the third switch <NUM> and the fourth switch <NUM>, and the switching loss may increase. When the voltage across the both ends of the flying capacitor <NUM> is clamped to the input voltage VIN or the ground voltage 0V, the control circuit <NUM> may reduce losses due to the current flowing through the body diodes inside the third switch <NUM> and the fourth switch <NUM>, by turning on the third switch <NUM> and the fourth switch <NUM>.

Since the voltage of the flying capacitor <NUM> is in the floating state, the control circuit <NUM> may detect the zero crossing point of the upper voltage VCA (e.g., the voltage of the first node <NUM>) of the flying capacitor <NUM> and the zero crossing point of the lower voltage VCB (e.g., the voltage of the third node <NUM>) without directly detecting the voltage of the flying capacitor <NUM>, and may determine the turn-on time of the third switch <NUM> and the fourth switch <NUM>.

In the first period T1, the fourth switch <NUM> may be turned on at the seventh time t7 when the voltage VCB of the third node <NUM> crosses to '<NUM>' (e.g., the voltage Vc of both ends of the flying capacitor <NUM> being clamped to the input voltage VIN). Accordingly, the fourth switch <NUM> may be turned on before the first switch <NUM> is turned off. The seventh time t7 may be a time point at which the body diode inside the fourth switch <NUM> starts to conduct.

In the second period T2, the third switch <NUM> may be turned on at the eighth time t8 when the voltage VCA of the first node <NUM> crosses to '<NUM>' (e.g., the voltage Vc of both ends of the flying capacitor <NUM> is clamped to the ground voltage 0V). Accordingly, the third switch <NUM> may be turned on before the second switch <NUM> is turned off. The eighth time t8 may be a time point at which the body diode inside the third switch <NUM> starts to conduct.

<FIG> illustrates a change in a switching signal of a current control method in a fourth state of a second mode, according to an embodiment.

Referring to <FIG>, the fourth state may be a state in which the zero current period of the inductor current IL (e.g., a period in which IL is '<NUM>') is included and the clamping occurs in the voltage across the both ends of the flying capacitor <NUM>.

The turn-on operation of the third switch <NUM> and the fourth switch <NUM> may be changed by a time point at which the voltage Vc across the both ends of the flying capacitor <NUM> is clamped to the input voltage VIN or the ground voltage 0V. The turn-on operation of the third switch <NUM> and the fourth switch <NUM> may be the same as that of <FIG>, and the turn-off operation of the third switch <NUM> and the fourth switch <NUM> may be the same as that of <FIG>.

In the first period T1, the fourth switch <NUM> may be turned on at the seventh time t7 when the voltage VCB of the third node <NUM> crosses to '<NUM>' (e.g., the voltage Vc across the both ends of the flying capacitor <NUM> being clamped to the input voltage VIN). The fourth switch <NUM> may be turned on before the first switch <NUM> is turned off.

In the first period T1, when the first switch <NUM> is in the turned on state at the fifth time t5 when the inductor current IL becomes '<NUM>' (e.g., the sensing voltage Vcs is '<NUM>'), the third switch <NUM> may be turned off. The third switch <NUM> may be turned off before the second switch <NUM> is turned on.

In the second period T2, the third switch <NUM> may be turned on at the eighth time t8 when the voltage VCA of the first node <NUM> is clamped to the ground voltage 0V. The third switch <NUM> may be turned on before the second switch <NUM> is turned off.

In the second period T2, when the second switch <NUM> is in the turned on state at the sixth time t6 when the inductor current IL becomes '<NUM>' (e.g., the sensing voltage Vcs is '<NUM>'), the fourth switch <NUM> may be turned off. The fourth switch <NUM> may be turned off before the first switch <NUM> is turned on.

The electronic device according to various embodiments disclosed in the disclosure may be various types of devices. The electronic device may include, for example, a portable communication device (e.g., a smartphone), a computer device, a portable multimedia device, a mobile medical appliance, a camera, a wearable device, or a home appliance. The electronic device according to an embodiment of the disclosure should not be limited to the above-mentioned devices.

According to various embodiments, an electronic device (e.g., the electronic device <NUM> of <FIG>, or the electronic device <NUM> of <FIG>) includes a battery , a power management module electrically connected to the battery and that manages a charging or a discharging of the battery , and a processor electrically connected to the power management module , and the power management module includes a first charging circuit that includes a first switch group, a first capacitor , and a first inductor , a second charging circuit that includes a second switch group , a second capacitor , and a second inductor , and a power path distributor that distributes power from a first external power supply device or a second external power supply device to the first charging circuit or the second charging circuit , and the power management module is configured to identify a connection between the power path distributor and one of the first external power supply device or the second external power supply device , to determine a type of the connected power supply device, to allow the first charging circuit and the second charging circuit to operate in a first mode that allows the first charging circuit and the second charging circuit to each have a fixed voltage conversion ratio such that the battery is charged, when the type of the connected power supply device is a first type, and to allow the first charging circuit and the second charging circuit to operate in a second mode that allows a voltage conversion ratio to be changed corresponding to a charging ratio of the battery such that the battery is charged, when the type of the connected power supply device is a second type.

According to various embodiments, the power management module may determine the type of the connected power supply device, based on a PD communication.

According to various embodiments, the power management module , in a first period of the first mode, may discharge the power of the first capacitor through the first inductor such that the battery may be charged, and the power management module , in a second period of the first mode, may discharge the power of the second capacitor through the second inductor such that the battery may be charged.

According to various embodiments, the power management module , in the first period, may allow the battery to be charged while charging the second capacitor, and wherein the power management module , in the second period, may allow the battery to be charged while charging the first capacitor.

According to various embodiments, the power path distributor may include a third switch group and a third capacitor, and the power management module , in the first mode, may allow the third capacitor to be charged to a specified voltage and to be operated.

According to various embodiments, the power management module , in the first mode, may control the third switch group such that a power terminal that supplies the power of the connected power supply device is connected to the second charging circuit , and the power management module , in the second mode, may control the third switch group such that the power terminal that supplies the power of the connected power supply device is connected to the first charging circuit.

According to various embodiments, the power management module , in the first mode, may be configured to control the first switch group and the second switch group , based on a signal having a fixed duty cycle.

According to various embodiments, the fixed duty cycle may be a duty cycle of <NUM>%.

According to various embodiments, the power management module , in the first mode, may allow the signal to have the same frequency as a first resonant frequency of the first capacitor and the first inductor or a second resonant frequency of the second capacitor and the second inductor.

According to various embodiments, the power management module , in the second mode, may be configured to control the first switch group or the second switch group , based on a signal having a variable duty cycle corresponding to the charging ratio of the battery.

According to various embodiments, the power management module may be configured to change the duty cycle of the signal, based on a PWM.

According to various embodiments, when the first external power supply device or the second external power supply device includes a circuit for controlling a constant voltage or a constant current for the battery , the power management module may determine the first external power supply device or the second external power supply device as the first type.

According to various embodiments, the power management module , in the second mode, may allow the first switch group or the second switch group to be switched in response to an intersection time between a control voltage corresponding to the charging ratio of the battery and a first triangle wave or a second triangle wave, and the second triangle wave may be a signal in which the first triangle wave is delayed by half a wavelength.

According to various embodiments, the power management module , in the second mode, may allow a part of the first switch group or the second switch group to be turned off in response to the intersection time between the control voltage and the first triangle wave.

According to various embodiments, the power management module , in the second mode, may allow a part of the first switch group or the second switch group to be turned on in response to the intersection time between the control voltage and the second triangle wave.

According to various embodiments, the power management module , in the second mode, may be configured to control the first switch group or the second switch group , based on a control signal having a variable duty cycle corresponding to a first inductor current flowing through the first inductor or a second inductor current flowing through the second inductor.

According to various embodiments, the power management module may allow a switching frequency of the first switch group to be changed based on the first inductor current, and the power management module may allow a switching frequency of the second switch group to be changed based on the second inductor current.

According to various embodiments, the power management module may allow the first switch group or the second switch group to be switched in response to an intersection time between one of a first band voltage obtained by applying a first hysteresis voltage to a control voltage corresponding to the charging ratio of the battery or a second band voltage obtained by applying a second hysteresis voltage to the control voltage and a sensing voltage corresponding to one of the first inductor current or the second inductor current.

According to various embodiments, the first switch group may include a first switch electrically connected between a power terminal to which power of the first external power supply device is supplied and a first node, a second switch electrically connected between the first node and the second node, a third switch electrically connected between the second node and a third node, and a fourth switch electrically connected between the third node and a ground part, and one end of the first capacitor may be connected to the first node, the other end of the first capacitor may be connected to the third node, one end of the first inductor may be connected to the second node, and the other end of the first inductor may be connected to a charging terminal of the battery.

According to various embodiments, the power management module may allow the first switch and the second switch to be turned on at different timings respectively by an intersection of the second band voltage and the sensing voltage, and the power management module may allow the first switch and the second switch to be turned off at different timings respectively by an intersection of the first band voltage and the sensing voltage.

According to various embodiments, the power management module may allow the third switch to be operated by a control signal having a phase opposite to a control signal of the second switch, and the power management module may allow the fourth switch to be operated by a control signal having a phase opposite to a control signal of the first switch.

According to various embodiments, the power management module may allow the third switch to be turned off when the sensing voltage becomes '<NUM>' before the second switch is turned on, and the power management module may allow the fourth switch to be turned off when the sensing voltage becomes '<NUM>' before the first switch is turned on.

According to various embodiments, the power management module may allow the third switch to be turned on when a voltage of the first node is the same as a ground voltage before the second switch is turned off, and the power management module may allow the fourth switch to be turned on when a voltage of the third node is the same as the ground voltage before the first switch is turned off.

A method according to various embodiments of the disclosure may be included and provided in a computer program product.

Claim 1:
An electronic device (<NUM>, <NUM>) comprising:
a battery (<NUM>, <NUM>); and
a power management module (<NUM>, <NUM>) electrically connected to the battery (<NUM>, <NUM>) and configured to manage a charging or a discharging of the battery (<NUM>, <NUM>);
wherein the power management module (<NUM>, <NUM>) includes:
a first charging circuit (<NUM>) configured to include a first switch group (<NUM>), a first capacitor (<NUM>), and a first inductor (<NUM>);
a second charging circuit (<NUM>) configured to include a second switch group (<NUM>), a second capacitor (<NUM>), and a second inductor (<NUM>); and
a power path distributor (<NUM>) configured to distribute power from a first external power supply device (<NUM>) or a second external power supply device (<NUM>) to the first charging circuit (<NUM>) or the second charging circuit (<NUM>), and
the electronic device (<NUM>, <NUM>) being characterized in that the power management module (<NUM>, <NUM>) is configured to:
identify a connection between the power path distributor (<NUM>) and one of the first external power supply device (<NUM>) or the second external power supply device (<NUM>);
determine a type of the connected power supply device (<NUM>, <NUM>);
when the type of the connected power supply device (<NUM>, <NUM>) is a first type, allow the first charging circuit (<NUM>) and the second charging circuit (<NUM>) to operate in a first mode that allows the first charging circuit (<NUM>) and the second charging circuit (<NUM>) to each have a fixed voltage conversion ratio such that the battery (<NUM>, <NUM>) is charged; and
when the type of the connected power supply device (<NUM>, <NUM>) is a second type, allow the first charging circuit (<NUM>) and the second charging circuit (<NUM>) to operate in a second mode that allows a voltage conversion ratio to be changed corresponding to a charging ratio of the battery (<NUM>, <NUM>) such that the battery (<NUM>, <NUM>) is charged.