Patent Description:
In recent years, railroad vehicles with high energy efficiency capable of large-scale transportation are attracting attention. More energy saving and improvement in efficiency are expected for railroad vehicles by introduction of a highly-efficient dynamo-electric machine, energy saving operation control, and control in accordance with the characteristics of the dynamo-electric machine.

As one of these types of techniques, a technique for improving the efficiency and reliability of a drive system for a railroad vehicle by individually controlling a plurality of dynamo-electric machines because the railroad vehicle obtains power by the plurality of dynamo-electric machines is being studied.

In order to improve the efficiency of a railroad vehicle, Patient Literature <NUM> proposes a control device for a railroad vehicle which has a configuration in which an AC circuit breaker is provided between a power conversion device and each of a plurality of dynamo-electric machines and a circuit breaker control unit for individually controlling the opening and closing of the AC circuit breaker based on an operation control command from a cab is provided and which is driven under operating conditions where the dynamo-electric machine is highly efficient by reducing the number of dynamo-electric machines to be driven in accordance with torque necessary for the vehicle.

In order to maintain the output torque of an electric vehicle even in an open operation, Patient Literature <NUM> proposes an electric vehicle control device in which when the temperature of a dynamo-electric machine exceeds or is determined to exceed a preset allowance value, in order to change into a torque command suppressing the temperature of the dynamo-electric machine within the allowance value, a dynamo-electric machine whose torque is supplemented is selected in the order in which the temperature has a margin among the other dynamo-electric machines, and the shortage of the output torque in the dynamo-electric machine where the temperature rises is compensated.

As a result of intensive studies for the purpose of further improving the efficiency of a drive device for a railroad vehicle, the inventors of the application have obtained the following findings.

However, there is a problem that the magnet magnetic flux increases and the efficiency is deteriorated as the temperature decreases due to operating conditions where an iron loss is dominant at the time of high-speed rotation and low torque In other words, it is not sufficient to realize high efficiency only by allocating the torque of the dynamo-electric machine in the order in which the temperature has a margin based on the temperature of the permanent magnet synchronous motor, and there is a possibility that the efficiency is deteriorated depending on operating conditions.

<NUM>) For the reasons described above, there is room for improvement to realize the high efficiency of a drive system using a plurality of dynamo-electric machines, in particular, permanent magnet synchronous motors.

An object of the present invention is to improve the efficiency of a system for obtaining, when driving and controlling a plurality of dynamo-electric machines, power by the plurality of dynamo-electric machines by individually changing a torque operation amount in consideration of the temperature dependency of the dynamo-electric machines. Solution to Problem.

The present invention provides a drive device for a dynamo-electric machine according to claim <NUM>. Further aspects of the invention are described by the remaining claims. Advantageous Effects of Invention.

According to the present invention, in a system driven by using a plurality of dynamo-electric machines, the high efficiency of the drive system can be realized and power consumption can be further reduced by individually changing the output torque of the plurality of dynamo-electric machines in consideration of the temperature dependency of the efficiency of the dynamo-electric machines.

Hereinafter, as forms of carrying out the present invention, first and second embodiments will be described in detail in accordance with the drawings. In each embodiment, requirements having the same reference numerals are shown as the same requirements or requirements having similar functions.

Note that configurations described below are merely presented as embodiments, and implementation modes according to the present invention are not limited to the following embodiments.

<FIG> is a diagram for showing an example of functional blocks of a drive device for a permanent magnet synchronous motor according to a first embodiment. A configuration for adjusting a torque command value is shown as functional blocks so that the total efficiency of a drive system configured using plural permanent magnet synchronous motors is enhanced based on temperature information of each permanent magnet synchronous motor.

Although two permanent magnet synchronous motors 4a and 4b are shown in <FIG>, the number of permanent magnet synchronous motors is not limited to two as long as plural motors are used. Hereinafter, components and functions related to two motors are distinguished by using subscripts a and b so as to correspond to two motors.

In addition, in <FIG>, electric power is transferred to and from an overhead wire <NUM> via a pantograph <NUM>, and a current between the overhead wire side and the permanent magnet synchronous motor side can be cut off by a high-speed circuit breaker <NUM> and a line breaker <NUM>. In addition, an LC filter circuit for smoothing a DC current that is configured using a filter reactor <NUM> and a filter capacitor <NUM> is provided between voltage generation devices 3a and 3b and the overhead wire <NUM>.

A control device for drive control of the permanent magnet synchronous motors includes an integrated control unit <NUM> and sub control units 2a and 2b. Based on switching commands from the sub control units 2a and 2b, the voltage generation devices 3a and 3b output voltages, and obtain power by allowing the permanent magnet synchronous motors 4a and 4b to output predetermined torque.

A torque calculation unit <NUM> included in the integrated control unit <NUM> outputs torque command values τm1* and τm2* to be generated in the permanent magnet synchronous motors 4a and 4b to the sub control units 2a and 2b, respectively, in accordance with a power command τm0* or a control mode switching command from a higher-level system control unit (not shown in the drawing).

Control programs for driving and controlling the permanent magnet synchronous motors 4a and 4b connected as loads are installed in the sub control units 2a and 2b. The sub control units 2a and 2b output switching commands SW<NUM> and SW<NUM> for outputting predetermined torque from the permanent magnet synchronous motors 4a and 4b. The voltage generation devices 3a and 3b perform switching control in response to the switching commands SW<NUM> and SW<NUM> and output voltages.

Here, <FIG> shows only the minimum functional blocks necessary for the first embodiment, and a power converter configured using power devices such as a driving transistor such as an IGBT (Insulated Gate Bipora Transistor) and a diode and a control configuration for the power converter are shown using the block diagrams of the voltage generation devices 3a and 3b, and detailed illustration thereof is omitted.

The permanent magnet synchronous motors 4a and 4b generate rotational torque by magnet torque generated by attraction and repulsion between a magnetic pole of a rotational magnetic field generated on the stator side by application of a three-phase AC voltage and a magnetic pole of a permanent magnet of a rotor, and reluctance torque generated by attraction force between the magnetic pole of the rotational magnetic field of the stator and a magnetic salient pole of the rotor.

Current detectors 5a and 5b detect waveforms of three-phase currents Iu1, Iv1, and Iw1 and Iu2, Iv2, and Iw2 of the U-phase, V-phase, and W-phase flowing in the permanent magnet synchronous motors 4a and 4b, respectively. However, it is not always necessary for the current detectors 5a and 5b to detect the currents of all the three phases, and any two phases among the three phases may be detected, and the remaining one phase may be obtained by calculation on the assumption that the three-phase currents are in an equilibrium state.

In addition, AC contactors 6a and 6b are provided between the voltage generation devices 3a and 3b and the permanent magnet synchronous motors 4a and 4b, and cut off the current when an abnormality occurs. Here, it is assumed that the AC contactors 6a and 6b open and close in accordance with control signals (not shown in the drawing) output from the integrated control unit <NUM> or the sub control units 2a and 2b.

The sub control units 2a and 2b estimate temperature information T1^ and T2^ of the permanent magnet synchronous motors 4a and 4b, respectively, by using the current detection values of the current detectors 5a and 5b, and transmit the same to the integrated control unit <NUM>.

In addition, as a modified example of the first embodiment, <FIG> shows a configuration in which temperature detectors 40a and 40b are installed in the permanent magnet synchronous motors 4a and 4b to detect the temperature information T1^ and T2^. In the temperature detection, a frame temperature, a winding temperature, a permanent magnet temperature, or the like may be detected.

Hereinafter, the relationship between the temperature and efficiency of the permanent magnet synchronous motor that is the main point of the present invention will be described.

Losses generated in the permanent magnet synchronous motor can be largely classified into a copper loss, a mechanical loss, and an iron loss. When it is assumed for the permanent magnet synchronous motor that the input electric power is Pin, the output electric power is Pout, the torque is τm, the copper loss is Ws, the iron loss is Wi, the mechanical loss is Wm, and the angular frequency of the mechanical angle of the dynamo-electric machine is ωm, the efficiency n of the permanent magnet synchronous motor is represented by Equation (<NUM>). [Equation <NUM>] <MAT>.

In addition, the torque τm of the permanent magnet synchronous motor is represented by Equation (<NUM>). [Equation <NUM>] <MAT>.

Here, m is the number of phases, Pm is the number of pole pairs, Ke is a magnet magnetic flux (power generation constant), Id is a d-axis current, Iq is a q-axis current, Ld is a d-axis inductance, and Lq is a q-axis inductance.

The first term in Equation (<NUM>) is the above-described magnet torque (torque generated by attraction and repulsion between the magnetic pole of the rotational magnetic field and the magnetic pole of the permanent magnet of the rotor), and the second term in Equation (<NUM>) is the above-described reluctance torque (torque generated by attraction force between the magnetic pole of the rotational magnetic field of the stator and the magnetic salient pole of the rotor).

It is well known that since the magnet torque is determined by the product of the magnet magnetic flux Ke and the q-axis current Iq, the magnet torque fluctuates due to the influence of the fluctuation of the magnet magnetic flux Ke, and the output torque increases or decreases. For example, a demagnetization of -<NUM>%/°C of the permanent magnet means that when the temperature rises by <NUM>, the magnet magnetic flux Ke decreases by <NUM>%. That is, it is often considered that the low-temperature condition in which the magnet magnetic flux increases results in a more highly efficient operation because the output torque of molecules in Equation (<NUM>) increases.

In order to improve the efficiency of the drive system based on such an idea, for example, it is conceivable to supplement torque in the order in which the temperature of the dynamo-electric machine has a margin by applying the technique described in Patent Literature <NUM> for realizing high efficiency.

However, the inventors focused on the temperature dependency of the loss indicated by the denominator of Equation (<NUM>) based on detailed study, and found that the permanent magnet synchronous motor with a low temperature does not simply becomes high efficiency, but becomes high efficiency in different operation regions at low and high temperatures depending on the operating conditions of torque and frequency.

Hereinafter, outlines of the copper loss Ws, the mechanical loss Wm, and the iron loss Wi and the temperature dependency thereof will be described.

The copper loss Ws is a loss generated in a stator winding, and can be calculated from the current value flowing in the permanent magnet synchronous motor and the resistance value. Regarding the temperature dependency of the copper loss Ws, since the resistance value is changed in accordance with the temperature coefficient of a material used for the stator winding, the resistance value increases and the copper loss Ws tends to increase as the temperature rises.

The mechanical loss Wm is generated by a pressure loss due to a cooling fan provided in the rotor, friction of a bearing supporting the rotor at a frame of the permanent magnet synchronous motor, or the like, and can be generally calculated as a function of a drive frequency. Regarding the temperature dependency of the mechanical loss Wm, strictly speaking, although there is a change in the viscosity of grease used for a bearing, the change can be ignored in the dynamo-electric machine for railroad vehicles. Therefore, the mechanical loss Wm of the dynamo-electric machine for railroad vehicles is often treated as not being affected by temperature.

The iron loss Wi is a magnetic loss corresponding to the area of a hysteresis loop when the magnetic flux in a magnetic material used for a stator core or a rotor core is changed by applying an AC magnetic field, and is defined as the sum of a hysteresis loss and an eddy current loss and can be generally calculated as a function of magnetic flux density and a frequency. Regarding the temperature dependency of the iron loss Wi, the magnet magnetic flux itself largely affecting the iron loss in the permanent magnet synchronous motor has temperature dependency, and demagnetizes at, for example, about -<NUM>%/°C when the temperature rises as described above.

Further, the hysteresis loss in the iron loss Wi is often considered to have substantially no temperature dependency. However, when the electric resistance of the iron core increases due to the temperature rise, the eddy current loss tends to decrease. Therefore, the iron loss Wi in the permanent magnet synchronous motor tends to decrease as the temperature becomes higher.

As described above, in terms of the loss in the permanent magnet synchronous motor, when the temperature is low, the copper loss decreases and the iron loss increases, whereas when the temperature is high, the copper loss increases and the iron loss decreases. That is, since the copper loss and the iron loss have a trade-off relationship with respect to the temperature, when considering a change in the loss at the time of temperature change under certain operating conditions, the loss as a dynamo-electric machine differently decreases under low or high temperature conditions depending on the ratio of the iron loss to the copper loss.

<FIG> are diagrams each showing the change characteristics of the ratio of the copper loss to the iron loss when the permanent magnet synchronous motors are driven at the same rotational speed and the torque and the temperature are changed.

<FIG> show calculation results by magnetic field analysis at the time of high torque, at the time of middle torque, and at the time of low torque, respectively, and the current value is adjusted so that the output torque becomes the same even when the temperature is changed. In addition, the values in each drawing are normalized by the loss under the temperature condition where the total of the copper loss and the iron loss is maximized under each condition. Note that the resistance and the magnet temperature are assumed to be similarly changed.

At the time of high torque, as shown in <FIG>, a large current flows under the operating condition of large torque, and thus the ratio of the copper loss becomes large with respect to <FIG>. In addition, when the temperature rises, an increase in the copper loss becomes larger than a decrease in the iron loss, and when the temperature of the permanent magnet synchronous motor becomes lower, the efficiency becomes higher.

The condition at the time of middle torque is, as shown in <FIG>, a condition where the load torque becomes smaller and the current becomes smaller than those in <FIG>, and thus when the temperature of the dynamo-electric machine is higher, the efficiency becomes slightly higher.

The condition at the time of low torque an operating condition where the torque is substantially <NUM>, and under such a condition, as shown in <FIG>, the total of the copper loss and the iron loss can be reduced by nearly <NUM>% when the temperature is high as compared to when the temperature is low.

That is, under the operating condition where the load torque is small, among the plurality of permanent magnet synchronous motors, the torque command value of the permanent magnet synchronous motor with a high temperature is intentionally increased, whereas the torque command value of the permanent magnet synchronous motor with a low temperature is decreased, so that it can be understood that the permanent magnet synchronous motors can be driven with high efficiency as a whole.

<FIG> are diagrams each showing the change characteristics of the ratio of the copper loss to the iron loss when the permanent magnet synchronous motors are driven with the same torque and the rotational speed and the temperature are changed.

<FIG> show calculation results by magnetic field analysis in a low-speed range, in a medium-speed range, and in a high-speed range, respectively, and the current is adjusted so that the output torque becomes the same even when the temperature is changed. In addition, the values in each drawing are normalized by the loss under the temperature condition where the total of the copper loss and the iron loss is maximized under each condition. Note that the resistance and the magnet temperature are assumed to be similarly changed.

In the low-speed range, as shown in <FIG>, the iron loss is small and the ratio of the copper loss accordingly becomes relatively higher in the operating condition where the rotational speed is low. In addition, when the temperature rises, an increase in the copper loss becomes larger than a decrease in the iron loss, and when the temperature of the permanent magnet synchronous motor becomes lower, the efficiency becomes higher.

The condition in the medium-speed range is, as shown in <FIG>, is a condition where the rotational speed is higher and the ratio of the iron loss becomes relatively larger than those in <FIG>, and thus is a region where the efficiency is not substantially changed even when the temperature of the dynamo-electric machine is changed.

In the high-speed range, the rotational speed is higher than that in <FIG>, and under such a condition, as shown in <FIG>, the total of the copper loss and the iron loss can be reduced by nearly <NUM>% when the temperature is high as compared to when the temperature is low.

That is, in an example not forming part of the invention, under the condition where the rotational speed is high, among the plurality of permanent magnet synchronous motors, the torque command value of the permanent magnet synchronous motor with a high temperature is intentionally increased, whereas the torque command value of the permanent magnet synchronous motor with a low temperature is decreased, so that it can be understood that the permanent magnet synchronous motors can be driven with high efficiency as a whole.

<FIG> is a diagram for showing an example of an operation region where the permanent magnet synchronous motor becomes highly efficient when the temperature of the permanent magnet synchronous motor is higher or lower than a reference value with respect to the speed (horizontal axis) and the torque (vertical axis).

As shown in <FIG>, when the median value of the specification range of temperatures is used as a reference, the region of high efficiency due to temperatures has a boundary with respect to the torque. In other words, when power is obtained by using at least two or more permanent magnet synchronous motors, the high efficiency of the system can be realized by changing the distribution of the torque command values so as to maximize the total efficiency in accordance with the temperature and torque.

Here, <FIG> are diagrams each showing an example of functional blocks of the torque calculation unit <NUM> provided in the integrated control unit <NUM> shown in <FIG>.

Specifically, the torque command values τm1* and τm2* shown in <FIG> will be described using <FIG>. As shown in <FIG>, the torque calculation unit <NUM> is configured by using torque operation amount calculation units <NUM>, and outputs the torque command value by adding a torque operation amount to the power command τm0* in accordance with a map indicating the efficiency of the permanent magnet synchronous motor at the time of temperature change or a calculation formula for obtaining the efficiency. The map indicating the efficiency or the calculation formula for obtaining the efficiency is derived from measured values or magnetic field analysis, and is recorded in a storage device (not shown in the drawing) appropriately provided in the integrated control unit <NUM> or the torque calculation unit <NUM>.

For example, when being applied to two motor units, as shown in (b), the torque command values τm1* and τm2* are calculated by adding Δτm1* and Δτm2* to the power command τm0*.

In addition, when being applied to four motor units, as shown in (c), the torque command values τm1*, τm2*, τm3*, and τm4* are calculated by adding Δτm1*, Δτm2*, Δτm3*, and Δτm4* to the power command τm0*.

The torque operation amount calculation units <NUM> discriminate the permanent magnet synchronous motor with high efficiency based on each of the temperature estimated values of the permanent magnet synchronous motors, and determines the torque operation amount from the discrimination result. However, in order not to change the total amount of torque output from the drive system with respect to the conventional configuration shown in <FIG>, as shown in <FIG> or <NUM>(c), the sum of torque compensation amounts is adjusted so as to be approximately <NUM> (Δτm1*+Δτm2*=<NUM> or Δτm1*+Δτm2*+Δτm3*+Δτm4*=<NUM>), in other words, the total amount of the torque command values in the drive system is adjusted so as to be approximately constant.

Here, the calculation of the operation amounts of the torque command values Δτm1* to Δτm4* shown in <FIG> and the compensation method thereof are merely examples, and if the configuration is such that each of the torque operation amounts is adjusted in accordance with the speed and the frequency in consideration of the temperature dependency of the dynamo-electric machine, the present invention is not limited that shown in <FIG>.

In addition, although the example of operating the torque command values is shown in the first embodiment, a configuration of operating the current command values or the voltage command values corresponding to the torque command values may be employed.

However, there is a concern that the temperature rises by actively using the dynamo-electric machine with a high temperature at the time of low torque or in the high-speed range. However, since a railroad vehicle does not continue a normal operation at the same frequency or the torque operating point and repeats stop, acceleration, deceleration, and stop operations, only the dynamo-electric machine with a high temperature is not unevenly driven, and thus abnormal heat generation or the like does not occur. However, when it is predicted that the temperature exceeds a temperature allowance value considering the irreversible demagnetization of the permanent magnet, a limiter for temperature is provided to stop the compensation without increasing the torque command value of the dynamo-electric machine with a high temperature.

On the other hand, in the case (not forming part of the invention) of a drive system using an induction motor as the dynamo-electric machine, since no permanent magnet is used as the dynamo-electric machine, the magnetic flux does not decrease when the temperature rises. Therefore, the iron loss (magnetic loss excluding the secondary copper loss generated in the rotor) becomes approximately constant regardless of the temperature. In other words, in the case of the induction motor, the total efficiency of the drive system can be improved by simply increasing the distribution of the torque commands to the dynamo-electric machine (induction motor) with a low temperature.

<FIG> is a diagram for showing an outline configuration of a part of a railroad vehicle on which the drive device for the permanent magnet synchronous motor according to the present invention is mounted. A plurality of permanent magnet synchronous motors 4a, 4b, 4c, and 4d driven by an inverter <NUM> is coupled to axles of the railroad vehicle via reduction gears (not shown in the drawing). The railroad vehicle travels by tangential force generated between wheels <NUM> connected to the axles and rails <NUM>.

In the railroad vehicle, the temperature varies depending on each dynamo-electric machine because control of changing the distribution of torque for each shaft with respect to the travel direction is used due to a change in the center of gravity according to the travel direction, because of the influence of the way the traveling wind blows against the dynamo-electric machine, and because of the influence of the state of defacement of a ventilation duct of the dynamo-electric machine. Therefore, by applying the present invention to a railroad vehicle, it is possible to obtain an effect of improving the efficiency of the drive system of the railroad vehicle.

As described above, in the first embodiment, it is possible to improve the total efficiency of a plurality of permanent magnet synchronous motors by individually changing the torque operation amount in consideration of the temperature dependency of each permanent magnet synchronous motor.

A second embodiment is different from the first embodiment in that an estimated magnet temperature at the time of zero-torque control during driving under sensorless control is used as the temperature information of the permanent magnet synchronous motor. Accordingly, the temperature sensors shown in <FIG> are not necessary, and the temperature of the permanent magnet can be robustly estimated against the constant error of the inductance and resistance of the permanent magnet synchronous motor.

<FIG> is a diagram for showing an example of functional blocks of a drive device for a permanent magnet synchronous motor according to a second embodiment.

The sub control unit 2a of the second embodiment includes a PWM control unit 7a, a coordinate converter 8a, a vector control unit 9a, a current command calculation unit 10a, a temperature estimation unit 11a, and a speed estimation unit 31a.

The current command calculation unit 10a outputs current command values Id1* and Iq1* based on a torque command value τm1* from the integrated control unit <NUM>.

The coordinate converter 8a converts three-phase currents Iu1, Iv1, and Iw1 of a permanent magnet synchronous motor <NUM> detected by the current detector 5a into dq coordinates of the rotating coordinate system by using a phase angle θ<NUM>, and outputs the same to the vector control unit 9a as Id1 and Iq1.

The vector control unit 9a outputs voltage command values Vd1* and Vq1* so as to converge the current deviation to <NUM> by PI (Proportional-Integral) control or the like so that a d-axis current detection value Id1 and a q-axis current detection value Iq1 match Id1* and Iq1*, respectively.

The PWM control unit 7a outputs a switching command SW<NUM> for controlling the voltage generation device 3a based on the voltage command values Vd1* and Vq1*.

The speed estimation unit 31a estimates the angular frequency ω<NUM>* of the rotor based on the current detection values Id1 and Iq1 and the voltage command values Vd1* and Vq1*.

The temperature estimation unit 11a outputs a magnet temperature estimated value T<NUM>^ or a magnet magnetic flux estimated value Ke1^ based on the current command values Id1* and Iq1* or the current detection values Id1 and Iq1, the voltage command values Vd1* and Vq1*, and the angular frequency ω<NUM>*. The magnet temperature and the magnet magnetic flux are calculated at a rate of -<NUM>%/°C with respect to a reference value, and either of them may be output as an estimated value. The magnet magnetic flux estimated value Ke1^ will be used in the following description.

In addition, since the block diagram inside the sub control unit 2b has the same configuration as that of the sub control unit 2a, the illustration thereof is omitted.

Hereinafter, the principle of estimating the temperature of the permanent magnet with high accuracy will be described. The voltage equations of the permanent magnet synchronous motor are represented by the following equations (<NUM>) and (<NUM>). [Equation <NUM>] <MAT> [Equation <NUM>] <MAT>.

If it is assumed that the state quantities of the actual voltage, current, resistance value, and inductance of the permanent magnet synchronous motor can be accurately grasped, the estimated value Ke^ of the magnetic flux can be calculated by Equation (<NUM>). [Equation <NUM>] <MAT>.

Considering the calculation of the constant Ke^ of the magnet magnetic flux in accordance with Equation (<NUM>), the voltage command values vd* and vq* of the voltage generation device <NUM> may be referred to for the voltages vd and vq, and the current detection values id and iq may be used for the currents. However, since a resistance r<NUM> and inductances Ld and Lq depend on the winding temperature of the permanent magnet synchronous motor, the magnetic saturation characteristics of a magnetic material used for the iron core, the motor structure, and the current conditions, it is difficult to accurately grasp them.

Thus, in order to estimate the magnet magnetic flux Ke without being affected by the constant error, the inventors have found that the magnet magnetic flux Ke can be estimated without being affected by the constant errors of the resistance r<NUM> and the inductances Ld and Lq by using the voltage command value vq* and the angular frequency ω<NUM>* in a control-stabilized state in a state where the torque shown in Equation (<NUM>) is controlled to be <NUM> while intentionally setting the current command values Id1* and Iq1* of the d-axis and the q-axis to <NUM>.

In Equations (<NUM>) and (<NUM>), when the current command values Id* and Iq* are set to <NUM> and the error of the current control by the vector control unit <NUM> is regarded as <NUM>, the voltage command values Vd* and vq* in a settled state are represented by the following equations (<NUM>) and (<NUM>). [Equation <NUM>] <MAT> [Equation <NUM>] <MAT>.

That is, the estimated value Ke^ of the magnet magnetic flux can be calculated by the following equation (<NUM>). [Equation <NUM>]<MAT>.

When the current command values Id* and Ip* are set to <NUM> and the error by the current control is <NUM>, the voltage command value Vq* of the q-axis is put in a state of outputting a voltage to cancel an induced voltage by the actual magnet magnetic flux Ke. Accordingly, it can be understood that Equation (<NUM>) does not include the terms of the resistance r<NUM> and the inductances Ld and Lq, and the voltage command value vq* can be calculated only by ω<NUM>* and Ke.

In addition, when a case in which the magnet magnetic flux fluctuates at the same frequency is exemplified, according to Equation (<NUM>), when the temperature of the permanent magnet rises and the actual magnet magnetic flux Ke decreases, Vq* in a settled state also decreases. On the other hand, when the temperature of the permanent magnet is lowered and the actual magnet magnetic flux Ke increases, Vq* in a settled state also increases. Thus, the magnet magnetic flux Ke can be estimated based on the q-axis voltage command value vq* when the current command values Id* and Iq* are set to <NUM>. However, according to Equation (<NUM>), the estimation method of the second embodiment cannot be applied in principle under the condition that the rotor speed ω<NUM> of the permanent magnet synchronous motor is <NUM>.

Here, in the estimation method of the second embodiment, since it is necessary that the current deviation by the current control is <NUM>, the drive control is performed by setting the current command values Id* and Iq* to <NUM>, and the q-axis voltage command value Vq* and the angular frequency command value ω<NUM>* in a state where the control is settled are used. In addition, in order to eliminate the influence of noise, a filtering process, a moving average process, or an integration process may be performed.

Next, the estimation of the magnet magnetic flux to be executed in the zero-torque control period is executed by using the zero-torque control period before the torque rising when the permanent magnet synchronous motor is restarted from the gate off and the free-run (coasting) of the rotor, or by using the zero-torque control period immediately before the gate off after the torque falling.

<FIG> is a diagram for showing a time flow in which the magnet magnetic flux is estimated during a zero-torque control period before the torque rising at the time of coasting restart. In addition, <FIG> is a diagram for showing a time flow in which the magnet magnetic flux is estimated during the zero-torque control period immediately before the gate off after the torque falling.

However, at the time of the zero-torque command, the current need not be exactly <NUM>, and a minute d-axis current may flow. In the voltage generation devices 3a and 3b, since a period in which upper and lower output elements are simultaneously turned off is provided in order to prevent short-circuit of elements such as IGBTs included in upper and lower arms provided in each phase, the output voltage during the simultaneous turning-off period becomes insufficient when voltage compensation is not applied. Therefore, a well-known dead time compensation technique is used to compensate the voltage command value so as to output the voltage in accordance with the command value based on the polarity of the current detection value or the current command value.

In particular, in a low speed region where the induced voltage of the permanent magnet synchronous motor is low and the modulation rate is low, a number of voltage pulses having a narrow width are output, so that the ratio of the simultaneous turning-off period to the output voltage becomes relatively large, and the influence on the output voltage is likely to become large.

That is, when both of the d-axis current command value Id* and the q-axis current command value Iq* shown in the first embodiment are set to <NUM> in the low speed region, if the polarity of the current detection value or the current command value used for the dead time compensation cannot be accurately grasped and the voltage is compensated based on the incorrect polarity as described above, the voltage error is adversely increased by the dead time compensation, and there is a possibility of deteriorating the estimation accuracy.

In response to this, a minute value is intentionally given to the d-axis current command value while setting the q-axis current command value to <NUM>, so that the polarity of the current command value or the current detection value can be determined. Accordingly, even at the time of the zero-torque command, the polarity of the current can be discriminated, the dead time compensation can be accurately operated, and the voltage output accuracy can be improved.

However, as shown in Equation (<NUM>), the magnitude of the minute current command value Id is set so that the magnetic flux (product of Ld and Id) due to the armature reaction is about <NUM>/<NUM> or less of the magnet magnetic flux Ke so as not to be affected by the constant error of the d-axis inductance Ld. For example, in the case of <NUM>/<NUM> or less, the magnitude of the minute current command value Id* may be set in the range of Equation (<NUM>) with respect to the set value (reference value) Ke* of the power generation constant and the d-axis inductance Ld* set in the controller. [Equation <NUM>] <MAT> [Equation <NUM>] <MAT> [Equation <NUM>] <MAT>.

Claim 1:
A drive device for a dynamo-electric machine, comprising:
a plurality of voltage generation devices (<NUM>) for outputting arbitrary voltages to a plurality of dynamo-electric machines (<NUM>); and
a control device (<NUM>) for adjusting the output voltages of the voltage generation devices (<NUM>),
wherein the control device (<NUM>) is configured to acquire the temperature of each of the plurality of dynamo-electric machines (<NUM>), to select a relatively highly-efficient dynamo-electric machine from among the plurality of dynamo-electric machines (<NUM>) based on each temperature, and to increase a torque command value of the selected dynamo-electric machine relative to the plurality of other dynamo-electric machines (<NUM>) ;
characterized in that the dynamo-electric machines (<NUM>) are permanent magnet synchronous motors (<NUM>), and
wherein the control device (<NUM>) is configured to select a motor with a relatively low temperature among the plurality of permanent magnet synchronous motors (<NUM>) when the torque command value is large, and is configured to select a motor with a relatively high temperature among the plurality of permanent magnet synchronous motors (<NUM>) when the torque command value is small.