Patent Document

This application is a division of application Ser. No. 09/356269 filed Jul. 16, 1999 now U.S. Pat. No. 6,151,272. 
    
    
     RELATED APPLICATION 
     This application is related to Korean Application No. 98-28847, filed Jul. 16, 1998, the disclosure of which is hereby incorporated herein by reference. 
     FIELD OF THE INVENTION 
     The present invention relates to integrated circuit devices, and more particularly to integrated circuit memory devices. 
     BACKGROUND OF THE INVENTION 
     Single data rate (SDR) synchronous DRAM integrated circuits have been developed in order to improve the performance of conventional dynamic random access memory (DRAM) integrated circuits. In additional, double data rate (DDR) synchronous DRAM integrated circuits have been developed in order to improve the performance of single data rate synchronous DRAM integrated circuits. Single data rate synchronous DRAM integrated circuit devices process one data value during one period of a clock signal. Double data rate synchronous DRAM integrated circuits process two data values during one period of a clock signal. Therefore, the double data rate synchronous DRAM integrated circuit can have a data processing speed twice as high as that of the single data rate synchronous DRAM integrated circuit. 
     Because the double data rate synchronous DRAM integrated circuit has a very high data processing speed, the performance of the double data rate synchronous DRAM integrated circuit typically cannot be tested with low speed data equipment. For example, the operating frequency of the double data rate synchronous DRAM integrated circuit presently is about 100 MHz and the operating frequency of conventional test equipment for testing a wafer on which DRAM integrated circuits are arranged presently is only about several MHz (e.g., 5 MHz). Also, since the double data rate synchronous DRAM integrated circuit has a specific pin called a data strobe, the double data rate synchronous DRAM integrated circuit typically can only be tested by enabling the data strobe pin from the outside. Since conventional test equipment typically does not have the capability of enabling the data strobe pin, double data rate synchronous DRAM integrated circuits typically cannot be tested with conventional test equipment. Thus, notwithstanding the advantages of double data rate SDRAM deices, there continues to be a need for improved techniques to test such devices using conventional test equipment. 
     SUMMARY OF THE INVENTION 
     It is therefore an object of the present invention to provide integrated circuit memory devices that can be accurately and reliably tested using conventional test equipment. 
     These and other objects, advantages and features of the present invention can be provided by a double data rate (DDR) synchronous dynamic random access memory device (SDRAM) that comprises a memory cell array and a mask signal generator that generates first and second internal data masking signals (e.g., DM_F, DM_S) during test mode, in response to at least one single data rate mode signal (e.g., CL 1 ). A data controller is also provided to pass input write data to the memory cell array when the first and second internal data masking signals are inactive during normal operation and mask at least a portion of the input write data from the memory cell array when one of the first and second internal data masking signals (e.g., DM_S) is active during test mode operation. This ability to mask data facilitates operation of the DDR SDRAM in a specialized single data rate (SDR) mode for testing using conventional test equipment. 
     Moreover, according to a preferred aspect of the present invention, the mask signal generator is responsive to first and second single data rate mode signals (CL 1 , BL 1 ) and comprises a buffer that has a data input that receives an external data strobe signal (DS) and a control input that receives one of the first and second single data rate mode signals (e.g., CL 1 ). The mask signal generator also preferably comprises an internal data strobe signal generator that receives as inputs a data strobe clock signal (PCLKDS) and an output of the buffer, and generates an internal data strobe signal (PDS). The mask signal generator may also comprise a NAND gate that receives as inputs an internal clock signal and one of the first and second single data rate mode signals (e.g., CL 1 ) and generates the data strobe clock signal (PCLKDS) in response thereto. A mask signal controller is also preferably provided. The mask signal controller generates first and second internal data masking signals (DM_F, DM_S) in response to the internal data strobe signal (PDS) and a data masking signal (DM). The mask signal controller is also responsive to one of the first and second single data rate mode signals (e.g., CL 1 ) and the data controller is responsive to the internal data strobe signal (PDS). 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is an electrical schematic of an integrated circuit memory device according to a first embodiment of the present invention. 
     FIG. 2 is an electrical schematic of a first controller according to the embodiment of FIGS. 1 and 5. 
     FIG. 3 is an electrical schematic of a second controller according to the embodiment of FIGS. 1 and 5. 
     FIG. 4 is a timing diagram that illustrates operation of the device of FIG.  1 . 
     FIG. 5 is an electrical schematic of an integrated circuit memory device according to a second embodiment of the present invention. 
     FIG. 6 is a timing diagram that illustrates operation of the device of FIG.  5 . 
     FIG. 7 is an electrical schematic of a preferred circuit for reading data from a memory cell array. 
     FIG. 8 is a timing diagram that illustrates operation of the circuit of FIG.  7 . 
    
    
     DESCRIPTION OF PREFERRED EMBODIMENTS 
     The present invention will now be described more fully hereinafter with reference to the accompanying drawings, in which preferred embodiments of the invention are shown. This invention may, however, be embodied in different forms and should not be construed as limited to the embodiments set forth herein. Rather, these embodiments are provided so that this disclosure will be thorough and complete, and will fully convey the scope of the invention to those skilled in the art. Like numbers refer to like elements throughout and signal lines and signals thereon may be referred to by the same reference symbols. 
     FIG. 1 is a circuit diagram of a double data rate synchronous DRAM integrated circuit according to a first embodiment of the present invention. Referring to FIG. 1, the double data rate synchronous DRAM integrated circuit according to the first embodiment of the present invention includes first and second buffers  111  and  151 , a pulse generator  121 , first and second logic circuits  131  and  141 , and first and second controllers  161  and  171 . The first buffer  111  receives as an input an external clock signal CLK and converts the voltage level of the external clock signal CLK. For example, the first buffer  111  converts the external clock signal CLK from a transistor logic (TTL) level into a clock signal of a complementary metal oxide semiconductor (CMOS) level. The pulse generator  121  accepts as an input the output from the first buffer  111  and generates an internal clock signal PCLK. The pulse generator  121  generates the internal clock signal PCLK whenever the external clock signal CLK rises from logic low to logic high. 
     The first logic circuit  131  receives as an input a first single data rate mode signal CL 1  input from the outside and the internal clock signal PCLK, and generates a data strobe clock signal PCLKDS. The first logic circuit  131  outputs the data strobe clock signal PCLKDS in response to the internal clock signal PCLK when the first single data rate mode signal CL 1  is activated to logic high, and does not generate the data strobe clock signal PCLKDS when the first single data rate mode signal CL 1  is deactivated to logic low. Namely, the first logic circuit  131  includes a NAND gate for performing a NAND operation on the internal clock signal PCLK and the first single data rate mode signal CL 1 . Therefore, the data strobe clock signal PCLKDS becomes logic high when either the internal clock signal POLK or the first single data rate mode signal CL 1  is logic low and becomes logic low when both the internal clock signal PCLK and the first single data rate mode signal CL 1  are logic high. The first single data rate mode signal CL 1  is activated when a column address strobe (CAS) latency is  1 . 
     The second buffer  151  receives as an input an external data strobe signal DS and the first single data rate mode signal CL 1 . The second buffer  151  changes the voltage level of the external data strobe signal DS in response to the first single data rate mode signal CL 1 . The second buffer  151  outputs logic high when the first single data rate mode signal CL 1  is activated to logic high, and generates an output in response to the external data strobe signal DS when the first single data rate mode signal CL 1  is deactivated to logic low. Namely, the output of the second buffer  151  becomes logic high when both the external data strobe signal DS is logic high and the first single data rate mode signal CL 1  is logic low, and becomes logic low when both the external data strobe signal DS is logic low and the first single data rate mode signal CL 1  is logic low. 
     The second logic circuit  141  receives as an input the output of the second buffer  151  and the data strobe clock signal PCLKDS, and generates an internal data strobe signal PDS. The second logic circuit  141  includes a NAND gate  143  for performing a NAND operation on the internal clock signal PCLK and the output of the second buffer  151 , and an inverter  145  for inverting the output of the NAND gate  143 . Therefore, the internal data strobe signal PDS becomes logic low when either the output of the second buffer  151  or the data strobe clock signal PCLKDS is logic low, and becomes logic high when both the output of the second buffer  151  and the data strobe clock signal PCLKDS are logic high. 
     The first controller  161  receives as an input a data masking signal DM, the internal clock signal PCLK, the internal data strobe signal PDS, a second single data rate mode signal BL 1  and a data masking enable signal DMEN. The first controller  161  generates a first internal masking signal DM_F and a second internal masking signal DM_S. The first controller  161  is synchronized with the internal clock signal PCLK and the internal data strobe signal PDS when the second single data rate mode signal BL 1  is deactivated to logic low, and generates the first and second internal masking signals DM_F and DM_S in response to the data masking signal DM. When the second single data rate mode signal BL 1  is activated to logic high, the first internal masking signal DM_F is generated in response to the data masking signal DM, and the second internal masking signal DM_S is activated to logic high. 
     The second controller  171  receives as an input data DINi, a buffer enable signal DINEN, the internal clock signal PCLK, the internal data strobe signal PDS, the first internal masking signal DM_F and the second internal masking signal DM_S. The second controller also outputs first data Did_F and second data Did_S. The second controller  171  is synchronized with a rising edge of the internal clock signal PCLK when the first internal masking signal DM_F is deactivated to logic low, and outputs the first data Did_F. The second controller  171  does not output the first data Did_F when the first internal masking signal DM_F is activated to logic high. The second controller  171  is synchronized with the falling edge of the internal clock signal PCLK when the second internal masking signal DM_S is deactivated, and outputs the second data Did_S. The second controller  171  does not output the second data Did_S when the second internal masking signal DM_S is activated to logic high. 
     FIG. 2 is a circuit diagram of the first controller  161  shown in FIG.  1 . Referring to FIG. 2, the first controller  161  includes a buffer  211 , first through fifth D flip-flops  221  through  225 , and an OR gate  231 . The buffer  211  receives as an input the data masking signal DM and is controlled by the data masking enable signal DMEN. Namely, the buffer  211  buffers the data masking signal DM when the data masking enable signal DMEN is activated to logic high, and does not generate an output when the data masking enable signal DMEN is disabled to logic low. 
     The first D flip-flop  221  receives as an input the output of the buffer  211  and the output of the buffer  211  is synchronized with the internal data strobe signal PDS. The second D flip-flop  222  receives as an input the output of the first D flip flop  221  and the output of the first D flip-flop  221  is synchronized with the inverted internal data strobe signal PDS. The third D flip-flop  223  receives as an input the output of the second D flip-flop  222  and the output of the third D flip-flop  223  (i.e., the first internal masking signal DM_F) is synchronized with the internal clock signal PCLK. The fourth D flip-flop  224  receives as an input the output of the buffer  211  and the output of the buffer  211  is synchronized with the inverted internal data strobe signal PDS. The fifth D flip-flop  225  receives as an input the output of the fourth D flip-flop  224  and the output of the fourth D flip-flop  224  is synchronized with the internal clock signal PCLK. 
     The OR gate  231  performs an OR operation on the output of the fifth D flip-flop  225  and the second single data rate mode signal BL 1 , and outputs the second internal masking signal DM_S. When either the output of the fifth D flip-flop  225  or the second single data rate mode signal BL 1  is logic high, the second internal masking signal DM_S becomes logic high. When both the output of the fifth D flip-flop  225  and the second single data rate mode signal BL 1  are logic low, the second internal masking signal DM_S becomes logic low. The second single data rate mode signal BL 1  is activated to logic high when the burst length of the double data rate synchronous DRAM integrated circuit is  1 . 
     FIG. 3 is a circuit diagram of the second controller  171  shown in FIG.  1 . Referring to FIG. 3, the second controller  171  includes buffers  311 ,  312 , and  313  and sixth through tenth D flip-flops  321  through  325 . The buffer  311  receives as an input the data DINi from the outside and outputs data PDINi, controlled by the buffer enable signal DINEN. Namely the buffer  311  buffers the data DINi when the buffer enable signal DINEN is activated to logic high and outputs the data PDINi, and does not generate the data PDINi when the buffer enable signal DINEN is deactivated to logic low. 
     The sixth D flip-flop  321  receives as an input the data PDINi and outputs the data PDINi, synchronized with the internal data strobe signal PDS. The seventh D flip-flop  322  receives as an input the output of the sixth D flip-flop  321  and outputs the data DiF_F, synchronized with the inverted internal data strobe signal PDS. The eighth D flip-flop  323  receives as an input the data DIF_F and outputs the data Di_F, synchronized with the internal clock signal PCLK. The ninth D flip-flop  324  receives as an input the data PDINi and outputs the data DiF_S, synchronized with the inverted internal data strobe signal PDS. The tenth D flip-flop  325  receives as an input the data DIF_S and outputs the data Di_S, synchronized with the internal clock signal PCLK. 
     The buffer  312  receives as an input the data Di_F and outputs the data Did_F, controlled by the first internal masking signal DM_F. Namely, the buffer  312  does not output the data Did_F when the first internal masking signal DM_F is activated to logic high, but outputs the data Did_F, which is the same as the data Di_F, when the first internal masking signal DM_F is deactivated to logic low. The buffer  313  receives as an input the data Di_S and outputs the data Did_S, controlled by the second internal masking signal DM_S. The buffer  313  does not output the data Did_S when the second internal masking signal DM_S is activated, but outputs the data Did_S, which is the same as the signal Di_S, when the second internal masking signal DM_S is deactivated at a logic low. 
     FIG. 4 is a timing diagram of signals that illustrates operation of the device of FIG.  1 . Referring to FIG. 4, when the first single data rate mode signal CL 1  is logic low, the internal clock signal PCLK is generated in sync with the rising edge of the external clock signal CLK and the data strobe clock signal PCLKDS is maintained at logic high. Then, when the first and second single data rate mode signals CL 1  and BL 1  become logic high, the data strobe clock signal PCLKDS is generated as an inverted version of the internal clock signal PCLK (i.e., as logic 0 pulses), and the internal data strobe signal PDS is generated in response to the data strobe clock signal PCLKDS. When the second single data rate mode signal BL 1  becomes logic high, the second internal masking signal DM_S becomes logic high from logic low. When the second internal masking signal DM_S becomes logic high, the second data Did_S is masked by the second internal masking signal DM_S. As a result, the data DINi that is received as an input from the outside of the second controller  171  it is not written in the synchronous DRAM integrated circuit. As described in FIGS. 1 through 4, when the first and second single data rate mode signals CL 1  and BL 1  are activated, the double data rate synchronous DRAM integrated circuit device operates in a single data rate mode. Therefore, it is possible to test a double data rate synchronous DRAM integrated circuit by writing data into the double data rate synchronous DRAM integrated circuit using low speed test equipment. 
     FIG. 5 is a circuit diagram of a double data rate synchronous DRAM integrated circuit according to a second embodiment of the present invention. Referring to FIG. 5, the double data rate synchronous DRAM integrated circuit according to the second embodiment of the present invention includes first and second buffers  511  and  551 , a pulse generator  521 , first and second logic circuits  531  and  541 , and first and second controllers  561  and  571 . Since the first and second buffers  511  and  551 , the first and second logic circuits  531  and  541 , and the first and second controllers  561  and  571  have the same structure and perform the same operations as those of the circuits shown in FlG.  1 , descriptions thereof will be omitted. The difference between the circuit shown in FIG.  1  and the circuit shown in FIG. 5 is in the pulse generator  121  of FIG.  1  and pulse generator  521  of FIG.  5 . 
     The pulse generator  521  receives as an input the output of the first buffer  511  and generates the internal clock signal PCLK. The pulse generator  521  generates the internal clock signal PCLK at the rising and falling edges of the external clock signal CLK. The pulse generator  521  includes a rising pulse generator  523 , a falling pulse generator  525 , and a logic device  527 . The rising pulse generator  523  receives as an input the output of the first buffer  511  and generates a pulse at the rising edge of the external clock signal CLK. The falling pulse generator  525  receives as an input the output of the first buffer  511  and a pulse control signal PDUAL received as an input and generates a pulse at the falling edge of the external clock signal CLK. Namely, the falling pulse generator  525  generates the pulse at the falling edge of the external clock signal CLK when the pulse control signal PDUAL is activated to a logic high and does not generate the pulse when the pulse control signal PDUAL is deactivated to a logic low. 
     The logic device  527  performs an OR operation on the output of the rising pulse generator  523  and the output of the falling pulse generator  525  and generates the internal clock signal PCLK. Accordingly, the logic device  527  outputs logic high when either the output of the rising pulse generator  523  or the output of the falling pulse generator  525  is logic high, and outputs logic low when both the output of the rising pulse generator  523  and the output of the falling pulse generator  525  are logic low. Therefore, when the pulse is generated in the rising pulse generator  523 , the logic portion  527  outputs the pulse received from the rising pulse generator  523 , and outputs the pulse generated in the falling pulse generator  525  when the pulse is received from the falling pulse generator  525 . 
     FIG. 6 is a timing diagram of signals that illustrate operation of the device of FIG.  5 . Referring to FIG. 6, commands are input at the rising and falling edges of the external clock signal CLK. Namely, the double data rate synchronous DRAM integrated circuit device operates in a dual edge clocking mode. When the pulse control signal PDUAL and the first single data rate mode signal CL 1  are logic high, the internal clock signal PCLK is generated at the rising and falling edges of the external clock signal CLK. When the internal clock signal PCLK is generated, the data strobe clock signal PCLKDS is generated as an inverted version of the internal clock signal PCLK. When the data PDINi (shown in FIG. 3) is input, the data Di_F (shown in FIG. 3) is generated, and the data Did_F is generated by the data signal Di_F (shown in FIG.  3 ). When the second single data rate mode signal BL 1  is logic high, the second internal masking signal DM_S becomes logic high. When the second internal masking signal DM_S becomes logic high, the data Did_S is not output and only the data Did_F is output even though the data PDINi is input. 
     Thus, as described in FIGS. 5 and 6, it is possible to operate the double data rate synchronous DRAM integrated circuit in a dual edge clocking mode (of the single data rate mode) by activating the first and second single data rate mode signals CL 1  and BL 1 . Therefore, it is possible to test the double data rate synchronous DRAM integrated circuit at double the speed of the circuit shown in FIG. 1, by writing the data at double the speed of the circuit shown in FIG. 1 into the double data rate synchronous DRAM integrated circuit device using the low speed test device. 
     FIG. 7 is a circuit diagram of a double data rate synchronous DRAM integrated circuit according to a third embodiment of the present invention. The circuit shown in FIG. 7 is configured for reading data from the double data rate synchronous DRAM integrated circuit by operating the double data rate synchronous DRAM integrated circuit in the single data rate mode using the low speed test equipment. Referring to FIG. 7, the double data rate synchronous DRAM integrated circuit according to the third embodiment includes a buffer  71   1 , a logic portion  721 , and a controller  731 . The buffer  711  receives as an input the external clock signal CLK and the inverted external clock signal CLKB, and outputs signals PCLKDQ_F and PCLKDQ_S. The logic portion  721  receives as an input the signals PCLKDQ_F and PCLKDQ_S and the first single data rate mode signal CL 1 , and generates first and second control signals CLKDQ_F and CLKDQ_S. The logic portion  721  generates the first and second control signals CLKDQ_F and CLKDQ_S in response to the external clock signal CLK when the first single data rate mode signal CL 1  is deactivated to logic low. The logic portion  721  activates the first control signal CLKDQ_F to logic high and deactivates the second control signal CLKDQ_S to logic low when the first single data rate mode signal CL 1  is activated to logic high. The first single data rate mode signal CL 1  is activated when the CAS latency of the double data rate synchronous DRAM integrated circuit is  1 . 
     The logic portion  721  includes logic circuits  723  and  724 , and logic circuits  726  and  727 . The logic circuits  723  and  724  respectively include a NOR gate  723  and an inverter  724 . The logic circuits  726  and  727  respectively include a NAND gate  726  and an inverter  727 . The NOR gate  723  receives as inputs the single data rate mode signal CL 1  and the signal PCLKDQ_F and performs a NOR operation on them. Namely, the NOR gate  723  outputs logic low when either the first single data rate mode signal CL 1  or the signal PCLKDQ_F is logic high, and outputs logic high when both the single data rate mode signal CL 1  and the signal PCLKDQ_F are logic low. The inverter  724  inverts the output of the NOR gate  723  and outputs a first control signal CLKDQ_F. The NAND gate  726  receives as inputs an inverted version of the first single data rate mode signal CL 1  and the signal PCLKDQ_S and performs a NAND operation on them. Namely, the NAND gate  726  outputs logic high when either the inverted version of the first single data rate mode signal CL 1  or the signal PCLKDQ_S is logic low, and outputs logic low when both the inverted version of the first single data rate mode signal CL 1  and the signal PCLKDQ_S are logic high. The inverter  727  inverts the output of the NAND gate  726  and outputs the second control signal CLKDQ_S. 
     A controller  731  receives as inputs the first and second data signals DB_F and DB_S and is controlled by the first and second control signals CLKDQ_F and CLKDQ_S. When the first and second control signals CLKDQ_F and CLKDQ_S are deactivated to logic low, the first and second data signals DB_F and DB_S are not output. When only the first control signal CLKDQ_F is activated to logic high, only the first data DB_F is output. When the first and second control signals CLKDQ_F and CLKDQ_S are activated to logic high, the first and second data signals DB_F and DB_S are output. The controller  731  includes first through third switching devices  741  through  743 , first and second latches  751  and  752  and an output inverter  761 . 
     The first switching device  741 , which receives as an input the first data DB_F and outputs the first data DB_F, is controlled by the first control signal CLKDQ_F. The first switching device  741  comprises an NMOS transistor to which the first control signal CLKDQ_F is applied at the gate and the first data DB_F is applied at the drain. Therefore, the first switching device  741  is turned on when the first control signal CLKDQ_F is logic high and outputs the first data DB_F. The first switching device is turned off when the first control signal CLKDQ_F is logic low and does not output the first data DB_F. The second switching device  742 , which receives as an input the second data DB_S and outputs the second data DB_S, is controlled by the first control signal CLKDQ_F. The second switching device  742  includes an NMOS transistor to which the first control signal CLKDQ_F is applied at the gate and the second data DB_S is applied at the drain. Therefore, the second switching device  742  is turned on when the first control signal CLKDQ_F is logic high and outputs the second data DB_S. The second switching device is turned off when the first control signal CLKDQ_F is logic low and does not output the second data DB_S. 
     The first latch  751  latches and outputs the output of the second switching device  742 . The third switching device  743 , which receives as an input the second data DB_S output from the first latch  751  and outputs the second data DB_S, is controlled by the second control signal CLKDQ_S. The third switching device  743  includes an NMOS transistor to which the second control signal CLKDQ_S is applied at the gate and the second data DB_S is applied at the drain. Therefore, the third switching device  743  is turned on when the second control signal CLKDQ_S is logic high and outputs the second data DB_S. The third switching device is turned off when the second control signal CLKDQ_S is logic low and does not output the second data DB_S. The second latch  752  inverts the first and second data DB_F and DB_S, respectively, output from the first and third switching devices  741  and  743 , and latches and outputs the first and second data. Output data DOi of the controller  731  is output from the second latch  752 . 
     FIG. 8 is a timing diagram of signals that illustrate operation of the device of FIG.  7 . Referring to FIG. 8, the internal clock signal PCLK is generated at the rising and falling edges of the external clock signal CLK. When the first single data rate mode signal CL 1  is logic high, the first control signal CLKDQ_F is activated to a logic high and the second control signal CLKDQ_S is deactivated to a logic low. When the first control signal CLKDQ_F is a logic high, the first data DB_F is output as the output data DOi of the controller  731 , however, the second data DB_S is not output as the output data DOi of the controller  731 . Thus, as described in FIGS. 7 and 8, when the first single data rate mode signal CL 1  is activated, the double data rate synchronous DRAM integrated circuit operates in the single data rate mode. Therefore, it is possible to test the double data rate synchronous DRAM integrated circuit by reading the internal data of the double data rate synchronous DRAM integrated circuit with the low speed test equipment. 
     According, as explained above with respect to FIGS. 1-8, it is possible to test the double data rate synchronous DRAM integrated circuit with the low speed test equipment by activating the first and second single data rate mode signals CL 1  and BL 1 , and operating the double data rate synchronous DRAM integrated circuit in the single data rate mode. 
     In the drawings and specification, there have been disclosed typical preferred embodiments of the invention and, although specific terms are employed, they are used in a generic and descriptive sense only and not for purposes of limitation, the scope of the invention being set forth in the following claims.

Technology Category: g