Patent Document

CROSS REFERENCE TO RELATED APPLICATION 
   This application claims the benefit and priority of U.S. provisional patent application entitled “CURRENT SENSING DRIVER OPERABLE IN LINEAR AND SATURATED REGIONS” (IR-1851 (2-2286)), filed May 14, 2003, Ser. No. 60/470,476, the entire disclosure of which is hereby incorporated by reference herein. 

   BACKGROUND OF THE INVENTION 
   The present invention relates to power MOSFETS, and in particular, to current sensing circuits for use with power MOSFETS which enable the current through the power MOSFET to be sensed in both the linear and saturated regions of MOSFET operation. 
   At the present time it is known to provide current sense structures for power MOSFETs which sense the drain-source current through the power MOSFET when the power MOSFET is in the saturated region, i.e., when the drain-source voltage is less than about 3 to 4 volts. When the drain source voltage is greater than 3 to 4 volts, the MOSFET is operating in the so-called linear region. Heretofore, current sense circuits have not been provided to sense the current when the power MOSFET operates in either the linear region or the saturated region. 
   It is an object of the present invention to provide a current sensing circuit for a power MOSFET which will sense the current in the power MOSFET in both the saturated and linear regions of operation. 
   SUMMARY OF THE INVENTION 
   The above and other objects of the invention are achieved by a circuit for sensing the current through a power MOSFET in both the linear and saturated regions of operation of the power MOSFET comprising a first circuit coupled to the power MOSFET for sensing the current through the power MOSFET in the saturated region of operation of the power MOSFET; and a second circuit coupled to the power MOSFET for sensing the current through the power MOSFET in the MOSFET&#39;s linear region of operation. 
   Other features and advantages of the present invention will become apparent from the following detailed description of the invention which refers to the accompanying drawings. 

   
     BRIEF DESCRIPTION OF THE DRAWING(S) 
     The invention will now be described in greater detail in the following detailed description with reference to the drawings in which: 
       FIG. 1  shows a power MOSFET including circuits for sensing the drain-source current of the MOSFET in both the linear and saturated regions; 
       FIG. 2  shows a a part of the circuit of  FIG. 1  for sensing the drain-source current in the power MOSFET in the saturated region of operation; and 
       FIG. 3  shows a part of the circuit of  FIG. 1  for sensing the drain-source current in the power MOSFET in the linear region of operation. 
   

   DETAILED DESCRIPTION OF THE INVENTION 
   With reference now to the drawings,  FIG. 1  shows a power MOSFET  20  which is provided with a main MOSFET cell or cells  20 A for conducting the load current as well as a current sense cell or cells  20 B for passing a much lower level of current, for example 10,000 times less current than in the main MOSFET, and which is proportional to the main MOSFET current, in this case, by a factor of 1/10,000. Two current sensing circuits are provided, the first circuit  10  for sensing current in the saturated region, and the second circuit  100  for sensing current in the linear region. The sensed current is detected as a voltage across a resistor RDG in each case. 
   Turning to  FIG. 2 , the circuit of  FIG. 1  for sensing current in the saturated region of operation is shown. In particular, the circuit shown operates when the drain-source voltage is less than approximately 3–4 volts. The power MOSFET is indicated at  20  and includes a main FET cell or cells  20 A and a current sense cell or cells  20 B. Load current I Load flows through the load as shown. A sense current isens is provided to the inverting input of an amplifier  22 . The source of the power MOSFET is provided to the non-inverting input of the amplifier  22 . The amplifier  22  is provided with positive and negative power supplies Vdd and Vss 2 . The output of the amplifier  22  is provided to an FET  24 , in this case a P-channel device  24 . The drain of device  24  is connected to a diagnostic output load, for example a resistor Rdg. The current through resistor Rdg will be proportional to the current I load through the load and the voltage across Rdg proportional to the load current I load. 
   The circuit operates as follows: When Vds of MOSFET cells  20 A is less than approximately 3–4 volts and because the amplifier  22  is biased between supply Vss 2  and the drain voltage Vdd, the amplifier provides an output only if the drain-source voltage of the power MOSFET is approximately less than 3–4 volts. Accordingly, the current through Rdg will be a measure of the current through the load only when the power MOSFET is on, not when the MOSFET is in its active clamp stage or during turn on or turn off, i.e., when the MOSFET is in its so-called linear mode and the drain-source voltage exceeds 3–4 volts. 
   The amplifier  22  sinks current from the current sense cells  20 B so that the voltage at the inverting input, i.e., voltage V isens  equals the voltage Vs at the non-inverting input V s . Once the voltages are equal at the inverting and non-inverting inputs, the current sense cells  20 B will have a voltage across them equal to the voltage Vds of the main power transistor. The current I sens is therefore proportional to the main cell  20 A current in the ratio of the cells in the sense cells  20 B to the main transistor cells  20 A. For example, the ratio 1/10,000. Accordingly, amplifier  22  will drive P-channel MOS device  24  sot that the voltage at the inverting input of amplifier  22  follows the voltage at the non-inverting input. The source of device  24 , connected to the amplifier inverting input, will sink the current I sens. The current through device  24  and thus through resistor Rdg will follow and the voltage across Rdg will be a measure of the current in the MOS device  20 A when it is in its saturated mode of operation i.e., when Vds is less than or equal to about 3–4 volts. Since the amplifier is biased between Vss 2  and the drain voltage, it only provides the diagnostic output when the voltage Vds is less than about 3–4 volts, i.e., when the power MOSFET is in its saturated region of operation. When Vds exceeds about 3–4 volts, the output is zero. 
     FIG. 3  shows the circuit  100  which is coupled to the power MOSFET to sense the current through the power MOSFET when it is in its linear region of operation, for example, when it is switching on or off and Vds is greater than about 3–4 volts. A resistor  101  is coupled in series with the current sense cell or cells of the power MOSFET. A further resistor  103  is provided in a current divider arrangement with the resistor  101 . First and second MOSFETs  105  and  107  are provided in a current mirror arrangement. A current source  109  is coupled to the current mirror arrangement. A third resistance  111  is coupled to the source of transistor  107  and mirrors the current through resistor  103  in a defined ratio. 
   The inverting input of an amplifier  122  is coupled to receive a voltage reference provided by a current source  124  coupled in series with a resistance R. The non-inverting input is coupled to the drain of the transistor  107  and to the drain potential Vdd of the main power MOSFET through a second resistor R. The output of the amplifier is coupled to first and second P-channel devices  126  and  128  having their gates coupled together and their sources connected to the drain potential of the main power MOSFET. The drain of device  126  is coupled to the source of transistor  107  and the drain of the second device  128  is coupled to the diagnostic output which is coupled to resistance RDG to ground. 
   The devices  126  and  128  are further provided so that the ratio of currents through the devices is in a defined ratio, e.g., in the ratio of 1 to 60, as shown. 
   The circuit operates as follows: 
   The current i 2  is proportional to the current i 1  in approximately the ratio of resistor  103  to resistor  111 . Due to the current mirror arrangement of transistors  105  and  107 , the current through resistor  111 , which is approximately equal to i 2 , will be approximately current i 1  times R 103 /R 111 . In the illustrated embodiment, R 103  is 150 ohms and R 111  is 4300 ohms. Due to the current ratio between devices  128  and  126 , IDG will be approximately equal to 60 times i 2  or 60 times R 103 /R 111  times i 1 . In the illustrated embodiment, this is approximately 2 times R 1 . The reason for the factor of 2 is that the voltage drop across the resistor  103  is large and affects the ratio of current i 1  to current I Load. This factor of 2 approximately corrects the I sens to source offset effect. To have the same ratio during linear mode and saturation mode can be achieved by trial changing the value of resistor  111 . To increase stability, IDG is driven in open loop. The resistor  101  has little influence because of its relatively high resistance compared to resistor  103  and protects against electrostatic discharge when the dies are unconnected. 
   When the current to the load increases, the current I sens also increases since the current sense cell  20 B is connected in series with parallel resistors  101  and  103  across the drain-source connection. The voltage across resistor  101  and accordingly across resistor  103  likewise increases, increasing the current through device  105  which is mirrored by device  107 . When the current through transistor  107  increases, the voltage at the non-inverting input of amplifier  122  decreases, driving the output of the amplifier  122  more negatively and biasing transistors  126  and  128  on more positively, increasing current i 2  and IDG. As current i 2  increases, the current in transistors  107  and  105  decrease reducing the voltage level on the non-inverting input until the voltages at the inputs to the amplifier are again equal. The voltage across resistor RDG will thus be proportional to the current through the main power MOSFET  20 A. 
   If Vds across the power MOSFET falls below about 3 to 4 volts, the sense circuit of  FIG. 2  senses the current from I sens so that the I sens-sk (source) voltage difference goes to 0 volts. The voltage across the resistors  101  and  103  thus goes to 0 and transistors  105  and  107  are thus turned off. Current i 2  drops to 0 so that the output of the circuit of  FIG. 3  is shut off and the circuit of  FIG. 2  then produces an output proportional to the current in the saturated region of operation of the MOSFET. 
   When the voltage Vds goes above approximately 3–4 volts, i.e., the power MOSFET is in the linear region, because of the biasing of amplifier  22  of  FIG. 2  between Vdd and Vss 2 , it ceases to provide an output and the circuit of  FIG. 3  provides an output (linear region). 
   Accordingly, the two circuits shown in  FIGS. 2 and 3  operate together such that the circuit of  FIG. 2  produces an output when the voltage across the power MOSFET is approximately 3 to 4 volts or less and the power MOSFET is operating in the saturation region and the circuit of  FIG. 3  operates when the voltage is above 3 to 4 volts and the MOSFET is in the linear region of operation. 
   Although the present invention has been described in relation to particular embodiments thereof, many other variations and modifications and other uses will become apparent to those skilled in the art. Therefore, the present invention should be limited not by the specific disclosure herein, but only by the appended claims.

Technology Category: g