Patent Document

This application is somewhat related to the commonly assigned U.S. application entitled &#34;Adaptive Transmit Preemphasis for Digital Modems&#34; 
     BACKGROUND OF THE INVENTION 
     1. Field of the Invention 
     The invention relates to a system for providing a modem user with a plot of the amplitude response of a channel such as a telephone line in the frequency band occupied by the modem signal without interrupting or otherwise affecting data signal traffic through the modem. 
     2. Description of the Prior Art 
     One of the many channel parameters affecting modem performance is the amplitude spectral characteristic of the channel. Severe band edge rolloff and ripples in the amplitude response can impair modem performance. Given spectrum information, the user can take appropriate action such as contacting the telephone company to correct telephone line problems. 
     In order to obtain the amplitude characteristics of a channel such as a telephone line, the modems on the line must be removed and test equipment installed at both ends of the line to make the meauurement. This method interrupts customer data traffic for the duration of the test. 
     SUMMARY OF THE INVENTION 
     The invention provides a user with a plot of the amplitude response of a channel such as a telephone line in the band occupied by the modem signal without interrupting or affecting data signal traffic through the modem. No test tones are required for M e  spectral measurements, i.e., the inventive circuit extracts spectral data from the actual received modem signal that has been shaped by the amplitude characteristics of the line. The amplitude characteristics are displayed on an external oscilloscope using a modem eye pattern display. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is a schematic of the non-interruptive spectrum analyzer system of the present invention. 
     FIGS. 2 and 3 respectively show reproductions of photographs of plots of a sampled output of the circuit of the present invention as compared to a measurement made with a Halcyon 520B3 telephone line tester. 
     FIG. 4 is a schematic of a portion of the circuit shown in FIG. 1. 
     FIG. 5 shows a schematic of a portion of the circuit of FIG. 1 with the addition of a double precision low-pass filter and an automatic gain control loop. 
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT 
     The invention provides a plot of the amplitude response of a telephone line by measuring the energy present at 32 frequencies from 300 Hz to 3400 Hz spaced 100 Hz apart. The data collected at the 32 points are stored in a 32 location memory buffer for display. A display function extracts the data from each of 32 memory locations at a rate sufficient to display a complete plot on an oscilloscope. 
     A block diagram of the inventive system is shown in FIG. 1. Analog receiver data signals are sampled by A/D converter 1 at a 9600 Hz rate. The sampled data are passed to the inventive circuit and to a modem demodulator for normal processing. In the inventive circuit the sampled data are mixed by the quadrature amplitude demodulator 2, 3 with oscillator 6 (not shown in FIG. 1), after it has been modified by sine and cosine lookup element 27, to provide the selected one of 32 frequencies. Oscillator 6 comprises a delay element 28 and a summer 29. The in-phase and quadrature data are filtered by low pass filters 4 and 5 respectively to remove the double frequency components of the mixing operation. Low pass filter 4 comprises multiplier element 30 for multiplying by a scaling constant and multiplier element 31 for multiplying by a filter constant, summers 32 and 33 and delay element 34. Low pass filter 5 comprises multiplier element 35 for multiplying by a scaling constant and multiplier element 36 for multiplying by a filter constant, summers 37 and 38, and delay element 39. The outputs of low pass filters 4 and 5 contain a DC output that is proportional to the instantaneous energy present at the frequency selected by oscillator 6. The outputs of LPFs 4 and 5 are sampled at a 300 Hz rate by sampler switches 40 and 41 (in order to reduce processor load) and squared by elements 7, 8. The outputs of squaring units 7 and 8 are summed and integrated by an ideal integrator 9. Integrator 9 has an input from summer 60 and consists of summer 61 and a delay element 44. Integrator 9 integrates the energy present at the selected frequency for 13 seconds in order to obtain an accurate measurement. At the end of the 13 second integration period switch 12 closes, the output of integrator 9 is converted to a logarithmic scale by converter 10 and the log value is stored in the appropriate frequency data memory locations in frequency data buffer 14. After the data is stored in buffer 14, integrator 9 is cleared, commutator 13 moves to the next frequency memory location in buffer 14, the frequency selection is incremented 100 Hz by integrator 18 which comprises delay element 42, and summer 43, and the integration begins at the new frequency. Switch 11 is used to load a constant into integrator 18. The constant is preselected so as to provide a 100 Hertz increment to the oscillator 6. This process repeats continuously updating all 32 memory locations. 
     In order to display the spectral measurements, the data in 14 must be presented at a much faster rate than it was stored. Thus, commutator 16 rotates through each of the 32 memory locations at a 2400 Hz rate. The digital data contained in the frequency memory location is converted to analog by D/A converter 22 and applied to the Y input of an external oscilloscope 24. Coincident with the movement of commutator 16, switch 17 closes to increment the X display offset generator 19 which comprises summer 45 and delay element 46. Device 19 generates a ramp that is scaled by elements 20, 21, converted to analog by D/A converter 23 and applied to the X input of oscilloscope 24. This X input spaces the 32 frequency data points to provide a display shown on oscilloscope 24 and FIGS. 2 and 3. 
     FIGS. 2 and 3 respectively show a sample output of the inventive circuit as compared to an output from Halcyon 520B3 telephone line tester. An important consideration is that the results achieved by the modem spectrum analyzer of the present invention as shown in FIG. 2 do not require the test tones which would be required for the measurements shown in FIG. 3. 
     The analyzer output can be converted to decibels by a log table to give greater dynamic range. A full scale log table can be implemented by shifting and counting shifts until the desired mantissa accuracy is achieved for a look-up table. The log scale can be computed each time a new frequency is selected. 
     With regard to the logarithmic conversion table shown below, the modem digital AGC word is scaled for 3 dB=hexadecimal 100. Numbers within the modem processor can be converted to the same scale by shifting and counting shifts to determine the characteristic, and then computing the mantissa by the look-up table. For each shift of V add hexadecimal 200 to the characteristic and for V 2  add hexadecimal 100. When the shifted value is less than hexadecimal 010 then look up the mantissa in a 16 entry table. An entry table is accurate to 1/2 dB. The output is 
     converted to dBs by the factors 3.01 dB/256 10 . 
     The following is a step by step summation of the procedure: 
     1. Compute V 2 . If V 2  is greater than or equal to 008 then dB=0 and exit. 
     2. Test if V 2  is less than 16 and skip to #5 if true. 
     3. Shift V 2  right (1/2) and add 256 to dB 
     4. Repeat 2 and 3 until test #2 passes. 
     5. Compute base address +V 2  -008. 
     6. Look up mantissa and add to dB for final value. 
     
         ______________________________________                            re-    man-V    V.sup.2 shift  dB Sum level mainder                                   tissa                                        level______________________________________2048 1024    7      1792   21 dB 15     232  2.73 dB1448 512     6      1536   18 dB 14     207  2.43 dB1024 256     5      1280   15 dB 13     179  2.11 dB 724 128     4      1024   12 dB 12     150  1.76 dB 512  64     3       768    9 dB 11     118  1.38 dB 362  32     2       512    6 dB 10      82  0.97 dB 256  16     1       256    3 dB  9      44  0.51 dB 181   8     0        0     0 dB  8      0   0.00 dB______________________________________ 
    
     FIG. 5 shows a schematic of a portion of the circuit of FIG. 1 with the addition of a double precision low pass filter and a Prairie Corporation automatic gain control loop. As with FIG. 4, elements which are the same as those shown in FIG. 1 have the same reference numerals. Additional elements include low pass filter 47, multiplier 48, summer 49, integrator 50, summer 51, transformer 52, modem digital automatic gain control module 53, and automatic gain control module 54. 
     The double precision filters are required for a band width on the order of 1 second in the loop. A small phase error is added to oscillator 50 to enable the &#34;tracking&#34;  filters to detect tones that may not be exactly on the sweep frequency which is generated in 100 Hz increments. The V 2  modules 40 and 50 require a double precision filter due to the wide dynamic range of V 2 . The modem automatic gain control AGC module 53 is added to the LOG scaled output for absolute calibration (3.01 dB/256 10 ). 
     Advantages of the aforestated invention include the fact that it improves on the prior art in not interrupting data traffic and not requiring external equipment to perform an amplitude spectral analysis. Integrating the diagnostic tools into the system itself not only provides more features for users but aids fields service personnel and users in problem solving without additional test equipment. 
     Although a preferred embodiment of the invention has been shown herein, it will be appreciated that many other embodiments can be contemplated within the scope of the appended claims.

Technology Category: 3