Patent Document

This Application is a Divisional of prior application Ser. No. 13/298,825, filed Nov. 17, 2011, currently pending. 
    
    
     Embodiments of the disclosure relate to memory circuits and specifically to a read assist circuits in static random access memories (SRAM). 
     BACKGROUND 
     Static random access memory (SRAM) has become the memory technology of choice for much of the solid-state data storage requirements in these modern power-conscious electronic systems. As is fundamental in the art, SRAM memory cells store contents “statically”, in that the stored data state remains latched in each cell so long as power is applied to the memory; this is in contrast to “dynamic” RAM (“DRAM”), in which the data are stored as charge on solid-state capacitors, and must be periodically refreshed in order to be retained. 
     Advances in semiconductor technology in recent years have enabled shrinking of minimum device feature sizes (e.g., MOS transistor gates) into the sub-micron range. This miniaturization is especially beneficial when applied to memory arrays, because of the large proportion of the overall chip area often devoted to on-chip memories. As a result, significant memory resources are now often integrated as embedded memory into larger-scale integrated circuits, such as microprocessors, digital signal processors, and “system-on-a-chip” integrated circuits. However, physical scaling of device sizes raises significant issues in connection with such embedded memory. 
     A problem encountered in connection with embedded SRAM memory now realized by modern manufacturing technology stems from the increased variability in the electrical characteristics of transistors formed at these extremely small feature sizes. This variability in characteristics has been observed to increase the likelihood of read and write functional failures, on a cell-to-cell basis. The combination of increased device variability with the larger number of memory cells (and thus transistors) within an integrated circuit renders a higher likelihood that one or more cells cannot be read or written as expected. 
     A particular failure mode that has been observed in conventional modern SRAM memories is the failure related to the switching of the state of an SRAM cell in a read operation. The read operation of an SRAM results in the internal node holding the zero to rise up due to the voltage division along the driver and pass transistor. When the rise is beyond a threshold, it can result in the bit flipping due to regenerative feedback and hence loss of stored data. 
     SUMMARY 
     An example embodiment provides a memory circuit. The memory circuit includes a bit cell that receives a word line, complementary bit lines and an array supply voltage; and a word line driver coupled to the word line. The word line driver receives one of the array supply voltage and a periphery supply voltage. A word line suppression circuit is coupled to the word line. The word line suppression circuit includes a diode and a switch coupled in series. The switch is responsive to the array supply voltage. In various embodiments, the bit cell includes an SRAM. 
     Another example embodiment provides memory circuit. The memory circuit includes a bit cell that receives a word line, complementary bit lines and an array supply voltage; and a word line driver coupled to the word line. The word line receives the array supply voltage. A word line suppression circuit is coupled to the word line. The word line suppression circuit includes a PMOS transistor coupled to the word line, and a diode and an NMOS transistor coupled in series, where the diode coupled to the word line. The NMOS transistor and the PMOS transistor are responsive to a control signal. 
     Another example embodiment provides a memory circuit. The memory circuit includes a bit cell receiving a word line, complementary bit lines and an array supply voltage; and a word line suppression circuit coupled to the word line that controls a slew rate of word line. The word line suppression circuit includes a pre word line driver and a final word line driver. 
     Other aspects and example embodiments are provided in the Drawings and the Detailed Description that follows. 
    
    
     
       BRIEF DESCRIPTION OF THE VIEWS OF DRAWINGS 
         FIG. 1  illustrates a 6T SRAM with a word line suppression circuit according to an embodiment; 
         FIG. 2  illustrates a 6T SRAM with a word line suppression circuit according to another embodiment; 
         FIG. 3  illustrates a 6T SRAM with a word line suppression circuit according to another embodiment; 
         FIG. 4  illustrates a 6T SRAM with a word line suppression circuit according to another embodiment; 
         FIG. 5  illustrates a timing diagram of the 6T SRAM of  FIG. 1 ; and 
         FIGS. 6   a  and  6   b  illustrate timing diagrams of the 6T SRAM of  FIG. 2  in read and write operations. 
     
    
    
     DETAILED DESCRIPTION OF THE EMBODIMENTS 
       FIG. 1  illustrates a memory circuit according to an embodiment. Specifically,  FIG. 1  illustrates a 6 transistor static random access memory (6T SRAM) with a word line suppression circuit  110  according to an embodiment. The 6T SRAM includes a word line driver  105  coupled to a word line (WL) on a line  165 . The word line driver  105  receives an address select signal on line  102  (one location in the range of locations that can store data in an SRAM) and an array supply voltage (hereinafter referred to as VDDAR). An output of the word line driver  105  is connected to the word line on the line  165 . The word line suppression circuit  110  includes a diode  120  connected in series to a switch  125  (it is noted that switch  125 , transistor  125  and NMOS switch  125  are used interchangeably in the description and they mean the same). In one embodiment the switch is an NMOS transistor, herein after referred to as transistor  125 . In other embodiments, a plurality of NMOS switches can be used instead on one NMOS switch. In one embodiment the diode ( 120 ) is an NMOS transistor, herein after referred to as transistor  120  (it is noted that transistor  120 , diode  120  and NMOS diode  120  are used interchangeably in the description and they mean the same). In other embodiments, a plurality of NMOS diodes can be used instead of one NMOS diode. A gate of the transistor  125  receives VDDAR on a line  170 . A bit cell  115  receives a word line, complementary bit lines (BL  155  and BLB  160 ) and VDDAR. The bit cell  115  (in an embodiment, the 6T SRAM) includes a pass transistor  130  with gate connected to the word line, drain connected to the BL and source connected to an inverter  140 . Similarly, the bit cell includes another pass transistor  150  with gate connected to the word line, drain connected to BLB and source connected to an inverter  145 . The inverter  140  includes a PMOS transistor (first load transistor) and an NMOS transistor  135  (first driver transistor). Source of the transistor  130  is connected to a node  132  which is defined between the drains of the PMOS and NMOS transistor ( 135 ) of the inverter  140 . Similarly an inverter  145  includes PMOS and NMOS transistor wherein gates of the transistors of the inverter  145  are also connected to the node  132 . 
     Operation of the SRAM is explained using the timing diagram as illustrated in  FIG. 5  and also using  FIG. 1 . Both read and write operations to the selected bit cells are performed by decoding the address which results in a word line (for example the word line  165 ) getting activated. In  FIG. 5 ,  515  indicates VDDAR. An address select signal ( 510 ) selects a word line  520  upon the rising edge of CLK signal  505  (shown as  535 ). A read cycle results in the contents of the bit cell  115  to be coupled to the complementary bit lines (BL  530  and BLB  525 ). Based on the contents of the bit cell (0/1) either of BL  530  or BLB  525  is pulled low by the bit cell action (shown as  540 ). A WRITE cycle results in the contents of the SRAM bit cell to be coupled from the complementary bit line (BL  155  and BLB  160 ). During a read or a write operation, a rising transition on the word line  165 , transistors  130  and  150  gets activated. When the transistors  130  and  150  are activated, and depending on the state of BL and BLB, the bit cell (formed by back to back connected inverters  140  and  145 ) is read from (read operation) or written into (write operation). When BL and BLB are pre-charged to high, before the onset of word line, the intended operation is read. When either of BL or BLB is pulled low to ensure the storage of the required state in the bit cell, then the intended operation is write. During a read ‘0’ operation, due to the activation of both the driver transistor  130  and pass transistor  135 , a resistive voltage drop occurs at node  136 . 
     Depending on the magnitude of the voltage drop at node  136 , the READ operation can manifest itself as an unwanted write operation when the value of the drop is sufficiently high to turn on the NMOS transistor in the inverter  145 , thereby causing the node  137  to drop. Because of the back to back connection of inverters  140  and  145 , a regenerative action develops and node  136  is pulled high resulting in the destruction of contents in the bit cell  115 . If the word line voltage is reduced, the voltage at the node  136  is also reduced during the read operation. In one embodiment reduction in word line voltage is achieved by a word line suppression circuit  110 . In other words, the word line suppression circuit  110  weakens the pass transistor  130  such that the voltage drop across the pass transistor  130  increases and the voltage drop between the pass transistor  130  and the driver transistor  135  reduces, thereby increasing the SNM. In an embodiment, there are several bit cells similar to bit cell  115  coupled to the word line  165  that also get activated by the same word line  165  and hence subject to the same word line suppression as explained above. 
     The need for word line suppression arises from the fact that a bit cell&#39;s ( 115 ) read operation is improved when the relative level of the word line reduces compared to the bit cell supply VDDAR. This results in the static noise margin (SNM) of the SRAM to be increased and hence ensures a robust read (it is noted that when SNM is high the read operation is more stable). In one embodiment, the word line suppression circuit  110  lowers the word line  165  by an amount determined by the sizing of the transistors  125  and  120  (diode). The term diode  120  and transistor  120  are used interchangeable and they refer to transistor  120 . Existing circuits achieve suppression using only NMOS diodes coupled to the word line, in which case the diode action limits the word line voltage to a value lesser than VDDAR and hence results in word line suppression. In one embodiment, the transistor  125  coupled to the NMOS transistor  120  results in self regulation of the word line  165  over process, temperature and voltage variations. Regulation of word line voltage for a bit cell that needs static noise margin (SNM) improvement is a key attribute to ensure successful read over PVT ranges. The lack of regulation can render the read operation to fail even in the presence of word line suppression due to insufficient SNM at some corners of the PTV combinations. 
     One solution to regulation achieved through additional NMOS diodes in series with NMOS diode  120  results in a trade-off between read current (hence read access time, performance) and successful READ operation over the PTV range, hence a sub-optimal solution. In an embodiment, regulation is achieved by the VGS (gate to source voltage) and VBS (body to source voltage) control of the NMOS diode  120  brought about by the suitable sizing of the NMOS switch  125  without compromising the read current. The current through the switch  125  remains constant over the PVT range because of the following phenomenon: when the threshold voltage of the NMOS diode  120  raises due to variation in PVT, the current through the NMOS switch  125  reduces resulting in a higher voltage drop across the NMOS switch  125 . When the voltage drop across the NMOS switch  125  increases, it lowers the VGS and VBS of the NMOS diode  120  and increases the current through the NMOS diode  120 , hence regulates the voltage drop of Word line  165 . The switch  125  provides the VGS and VBS control to the diode  120 . On the other hand, lowering of the threshold voltage of NMOS diode  120  raises the current through NMOS switch  125  which reduces the voltages drop across NMOS switch  125  with respect to the ground and hence increases the VGS and VBS of the NMOS diode  120 . This reduces the current through NMOS diode  120  and hence adjusts the voltage drop of the word line  165 . This explains the utility of the NMOS switch  125  compared to only NMOS diode  120  coupled to the word line voltage  165 . 
     Another embodiment of the invention is illustrated in  FIG. 2  having a 6T SRAM with a word line suppression circuit  210 . The 6T SRAM with the word line suppression circuit in  FIG. 2  is analogous to that of in  FIG. 1 . The word line driver  105  and the bit cell  115  is the same in connection as well as operation and are not explained again.  FIG. 2  also includes a control circuit  205  that receives a clock signal (CLK) and read/write selection (WZ). The control circuit  210  is preprogrammed to generate the control signal  280 .  FIG. 2  also includes the word line suppression circuit  210  connected to the word line  220 . The word line suppression circuit  210  includes a diode  230  connected in series to a switch  235 . In one embodiment, the switch is an NMOS transistor, herein after referred to as transistor  235 . In other embodiments, a plurality of NMOS switches can be used instead on one NMOS switch. In one embodiment the diode is an NMOS transistor, hereinafter referred to as transistor  230 . In other embodiments, a plurality of NMOS diodes can be used instead of one NMOS diode. A gate of the transistor  235  receives a control signal  280  generated by the control circuit  205 . The control signal  280  is also connected to PMOS transistor  225  having a source connected to VDDAR and drain coupled to the word line  220 . 
     During a read operation, the control signal  280  activates the NMOS transistor  235  and diode  230 , and deactivates the PMOS transistor  225 . During the READ operation, the circuit operations in  FIG. 1  and  FIG. 2  are the same as far as the bit cell  115  is concerned. However, during a first write operation the control signal  280  activates the NMOS transistor  235  and diode  230 , and deactivates the PMOS transistor  225 . During the second write operation, control signal  280  activates the PMOS transistor, and deactivates the diode  230  and the NMOS transistor  235 . It is noted that the first write operation and second write operation are two parts of the same write operation. The need for two part write operation arises from the fact that the bit cell coupled to the word line, but not intended/selected for a write operation undergoes a default read operation and hence subject to the same SNM issue as explained in the description of  FIG. 1 . In order to protect the contents of these bit cells, the first write operation provides the same word line suppression as in a read operation. The word line suppression circuit  210  is deactivated during the second write operation (using the control signal  280 ) in order to benefit the write operation for the selected bit cell  115 . Also, during the write operation, the word line is not suppressed in  FIG. 2  compared to  FIG. 1  using control signal  280 . 
     In an embodiment, there are several bit cells similar to bit cell  115  coupled to the word line  220  that also gets activated by the same word line  220  and hence subject to the same word line suppression as explained above. 
     Operation of the circuit in  FIG. 2  is now explained in detail using the timing diagram of  FIGS. 6A and 6B . Both read and write operations to the selected SRAM cells (bit cell  115 ) is performed by decoding the address which results in a word line  625   a  getting activated. The WZ  605   a  is high which indicates that it is a read operation. In  FIG. 6A , an address signal  615  selects a word line  625   a  upon the rising edge of CLK signal  610   a  (shown as  645 ). Based on the contents of the bit either BL  635   a  or BLB  630   a  will go low (shown as  650 ). Control signal  640   a  is generated based on WZ  605   a  and the CLK signal  610   a  and intended to be high during the positive level of the clock in one implementation. It is noted that the CLK signal  610   a  can be in a negative level in another implementation with accordingly synchronized appropriate signals at the falling edge of the CLK signal  610   a.    
     Referring to  FIG. 6B  now, the WZ  605   a  being low indicates that it is a write operation. An address signal  615   b  selects a word line  625   b  upon the rising edge of CLK signal  610   b  as part of the first write operation  660  (shown as  655 ). Based on the contents of BL  635   b  or BLB  640   b , the bit cell will get written with a 1 or a 0. Control signal  630   b  is generated based on WZ  605   b  and the CLK signal  610   b  and intended to be high during the first write operation and then to be low in the second write operation  665 . During the first write operation  660 , when the control signal  630   b  is high, the additional bit cells (that may be coupled to the same word line  625   b  and not shown in  FIG. 2 ), not selected for write operation also gets the benefit of word line suppression circuit  210  due to the control signal  630   b  being high. This ensures that the contents of the additional bit cells are not disturbed due to the write operation on the bit cell  115 . After the falling transition of the control signal  630   b , as shown as  665  in  FIG. 6   b , the control signal  630   b  turns off the transistor  235  and the word line suppression circuit  210 , turns on transistor  225  thereby restoring the word line  625   b  to the level of VDDAR  620   b . It is noted that the CLK signal  610   b  can be in a negative level in another implementation with accordingly synchronized appropriate signals at the falling edge of the CLK signal  610   b.    
       FIG. 3  illustrates a 6T SRAM with a word line suppression circuit according to another embodiment.  FIG. 3  includes a bit cell  315  receiving a word line (on the line  350 ), complementary bit lines (BL and BLB) and an array supply voltage (VDDAR). A word line suppression circuit  302  is coupled to the word line that controls a slew rate of word line. The word line suppression circuit  302  includes a pre word line driver  305  and a final word line driver  310 . The bit cell  315  is analogous to the bit cell  115  in connection as well as operation and is not repeated. The pre word line driver  305  receives an address select signal on line  355 . The pre word line driver  305  includes, in one example embodiment, three inverters  330  (first delay element),  325  (second delay element) and  320 , each of the inventers receive the address select signal. Each of the inventers are formed by gate connected PMOS transistor and NMOS transistor. The final word line driver  310  includes two PMOS transistors  335  and  340  and an NMOS transistor  345 . In one embodiment, the NMOS transistor of the inverter  325  is a strong NMOS transistor compared to the NMOS transistor of the inverter  330 . In various embodiments a strong transistor is defined as having higher W/L ration where W is the channel width and L is the channel length of the transistor. In various embodiments, a strong transistor can have a lower threshold voltage thereby having an ON current. Similarly, the PMOS transistor  335  is a strong transistor compared to the PMOS transistor  340 . Gates of the transistors  335  and  340  are controlled by the control signals which are generated as outputs from the inventers  330  and  335  respectively. The drains of the PMOS transistors  335  and  340  are coupled to the word line  350 . The final word line driver  310  also includes an NMOS transistor  345  having a drain coupled to the word line  350  and a source coupled to ground. Gate of the NMOS transistor  345  is controlled by an output of the inverter  320 . 
     The control signals on lines  304  and  306  are delayed with respect to each other dependant on sizes of the PMOS transistors  335  and  340  of the final word line driver  310 . The PMOS transistor  335  is activated prior to activating the PMOS transistor  340  by delaying the control signal on the line  306  with respect to the control signal on the line  304  such that a slew rate of the word line is controlled. Due to the fact that the NMOS of inverter  325  is stronger compared to the NMOS of the inverter  330 , a falling edge of the control signal ( 306 ) arrives earlier than that of the control signal  304 . This ensures that the PMOS transistor  340  is activated prior to PMOS transistor  335 . Because of prior activation of the weaker transistor  340  compared to the transistor  335 , the transistor  340  pulls up the word line  350  prior to the transistor  335 . However, since the transistor  340  is weaker compared to  335 , the slew rate of the word line  350  will be higher compared to the slew rate if the transistor  335  was to pull up the word line  350 . This phase of activation of transistor  340  form a first phase of the two phases of the word line activation. The poor slew rate during the first phase of word line activation acts as a word line suppression mechanism and therefore helps the bit cell  315  to overcome the problem of SNM as explained earlier in conjunction with  FIG. 1 . Upon the activation of PMOS transistor  335 , the slew rate of word line  350  is improved in the second phase of word line activation due to the higher strength of the transistor  335 . Higher slew rate of the world line  350  helps to alleviate the effect of word line suppression on the write operation. 
       FIG. 4  illustrates a 6T SRAM with a word line suppression circuit according to another embodiment.  FIG. 4  includes a bit cell  415  receiving a word line (on the line  450 ), complementary bit lines (BL and BLB) and an array supply voltage (VDDAR). A word line suppression circuit  402  is coupled to the word line  450  that controls a slew rate of word line. The word line suppression circuit  402  includes a pre word line driver  405  and a final word line driver  410 . The bit cell  415  is analogous to the bit cells  115  and  315  in connection as well as operation and is not repeated. The final word line driver  410  includes two PMOS transistors  445  and  440  and an NMOS transistor  435 . Similarly, the PMOS transistor  445  is a strong transistor compared to the PMOS transistor  440 . Gates of the transistors  440  and  445  are controlled by the control signals which are generated as outputs from the inventers  420  and  430  respectively. The drains of the PMOS transistors  440  and  445  are coupled to the word line  450 . The final word line driver  410  also includes an NMOS transistor  435  having a drain coupled to the word line  450  and a source coupled to ground. Gate of the NMOS transistor  435  is controlled by an output of the inverter  415 . The pre word line driver  405  receives an address select signal on line  455 . The pre word line driver  405  includes, in one example embodiment, four inverters, where inverters  420  (inverter  420  forming a first delay element),  425  and  430  (inverters  425  and  430  forming a second delay element) forming a delay chain  408 . Inverters  420  and  415  receive the address select signal on line  455 . Each of the inventers are formed by gate connected PMOS transistor and NMOS transistor. Two control signals are generated from the pre word lie driver  405 , one from the output of the delay chain  408  on the line  404  and the other from the output of the inverter  420  on line  406 . Gate of the transistor  445  receives the control signal on the line  404  and gate of the transistor  440  receives the control signal on the line  406 . 
     The control signals on lines  404  and  406  are delayed with respect to each other by selecting the outputs (control singles) from different points of the delay chain  408 . The PMOS transistor  440  is activated prior to activating the PMOS transistor  445  by delaying the control signal on the line  404  with respect to the control signal on the line  406  such that a slew rate of the word line is controlled. Due to the fact that a falling edge of the control signal  406  arrives earlier than that of the control signal  304 , the transistor  440  pulls up the word line  450  prior to the transistor  445 . However, since the transistor  440  is weaker compared to  445 , the slew rate of the word line  450  will be higher compared to the slew rate if the transistor  445  was to pull up the word line  450 . This phase of activation of transistor  440  forms a first phase of the two phases of the word line activation. The poor slew rate during the first phase of word line activation acts as a word line suppression mechanism and therefore helps the bit cell  415  to overcome the problem of SNM as explained earlier in conjunction with  FIG. 1 . Upon the activation of PMOS transistor  445 , the slew rate of word line  450  is improved in the second phase of word line activation due to the higher strength of the transistor  445 . Higher slew rate of the world line  450  helps to alleviate the effect of word line suppression on the write operation. 
     In the foregoing discussion, the term “connected” means at least either a direct electrical connection between the devices connected or an indirect connection through one or more passive or active intermediary devices. The term “circuit” means at least either a single component or a multiplicity of components, either active or passive, that are connected together to provide a desired function. The term “signal” means at least one current, voltage, charge, data, or other signal. It is to be understood that the term transistor can refer to devices including MOSFET, PMOS, and NMOS transistors. Furthermore, the term transistor can refer to any array of transistor devices arranged to act as a single transistor. 
     The forgoing description sets forth numerous specific details to convey a thorough understanding of the invention. However, it will be apparent to one skilled in the art that the invention may be practiced without these specific details. Well-known features are sometimes not described in detail in order to avoid obscuring the invention. Other variations and embodiments are possible in light of above teachings, and it is thus intended that the scope of invention not be limited by this Detailed Description, but only by the following Claims.

Technology Category: g