Patent Document

BACKGROUND 
     The present disclosure relates to a synchronizing circuit, a synchronizing method, and a receiving system. More particularly, the disclosure relates to a synchronizing circuit, a synchronizing method, and a receiving system capable of searching for optimum loop gains in keeping with the individual differences between receivers and the time jitter over transmission channels, even where a plurality of modulation techniques are used in a transmission frame. 
     The recent years have witnessed phenomenal progress in wireless digital transmission technologies including mobile phones, digital broadcasts (satellite and terrestrial), and wireless LAN&#39;s. 
     With regard to the receiver used for wireless digital transmission, for example, the performance of each synchronizing circuit making up the receiver structure is important in realizing enhanced reception performance. In particular, the synchronization performance of a carrier frequency/phase synchronizing circuit directly affects bit errors and is thus critically important for the reception performance of the receiver. 
     A representative frequency/phase synchronizing circuit may be the digital PLL (phase-locked loop). 
     The frequency/phase synchronizing circuit that uses the digital PLL is generally composed of a phase error detector, a loop filter, and a numerically controlled oscillator (NCO). 
       FIG. 1  is a schematic view showing a partial structure of an ordinary receiver that includes the frequency/phase synchronizing circuit utilizing the digital PLL. 
     As shown in  FIG. 1 , the receiver includes a radio frequency (RF) circuit  2  and a demodulation circuit  3 . A reception signal obtained by an antenna  1  receiving radio waves is input to a multiplier  2 - 1  of the RF circuit  2 . 
     The multiplier  2 - 1  multiplies a local oscillation signal supplied from a local oscillator  2 - 2  by the reception signal fed from the antenna  1 . The signal obtained through multiplication is forwarded to a low-pass filter (LPF)  2 - 3 . 
     The local oscillator  2 - 2  generates the local oscillation signal and outputs it to the multiplier  2 - 1 . 
     The LPF  2 - 3  inputs the multiplication signal output from the multiplier  2 - 1  and allows only the low-frequency component of the signal to pass through in a filtering process. The signal having undergone the filtering process is output to an analog/digital (A/D) converter  2 - 4 . 
     It is assumed here that reference character f c  stands for the frequency of the reception signal having undergone modulation such as PSK (Phase Shift Keying), θ c  for the phase of the reception signal, f 0  for the frequency of the local oscillation signal generated by the local oscillator  2 - 2 , and θ 0  for the phase of the local oscillation frequency. On that assumption, the signal output from the LPF includes a frequency difference Δf corresponding to f c -f 0  and a phase difference θ corresponding to θ c -θ 0 . 
     The A/D converter  2 - 4  performs A/D conversion on the signal output from the LPF  2 - 3 . The reception signal ri, which is a digital reception signal obtained through A/D conversion, is fed to the demodulation circuit  3 . The reference character i denotes the ordinal position of the reception signal in question in the sequence of symbols. 
     The reception signal ri contains a phase error represented by 2πΔft+θ. 
       FIG. 2  is a schematic view showing a typical structure of a frequency/phase synchronizing circuit that uses a digital PLL and that is furnished in the demodulation circuit  3  of  FIG. 1 . 
     As shown in  FIG. 2 , the frequency/phase synchronizing circuit is made up of a PLL circuit  11  and a multiplier  12 . The PLL circuit  11  is composed of a multiplier  21 , a phase error detector  22 , a loop filter  23 , and a numerically controlled oscillator (NCO)  24 . 
     The reception signal ri having undergone PSK modulation is input to the multiplier  21  of the PLL circuit  11  and to the multiplier  12 . 
     The multiplier  21  of the PLL circuit  11  multiplies the reception signal ri by a phase control amount e −j(2πΔft+θ)  supplied from the numerically controlled oscillator  24 . The signal obtained through multiplication is output to the phase error detector  22 . 
     The phase error detector  22  detects a phase error that may remain in the signal output from the multiplier  21 , and outputs the detected phase error to the loop filter  23 . 
     For example, if the reception signal ri is the signal of a known symbol, the phase error detector  22  detects as the phase error the difference between the phase of a symbol represented by the output signal from the multiplier  21  and the phase of the known symbol. If the reception signal ri is not the signal of any known signal, the phase error detector  22  detects as the phase error the difference between the phase of the actual symbol represented by the output signal from the multiplier  21  and the phase of a symbol resulting from hard decision. 
     The loop filter  23  is a proportional integral loop filter that filters the detected phase error value supplied from the phase error detector  22 . The filtered value is output to the numerically controlled oscillator  24 . 
     More specifically, a multiplier  23 - 1  of the loop filter  23  multiplies the detected phase error value fed from the phase error detector  22  by a previously established loop gain G 1 . The result of the multiplication is output to a multiplier  23 - 2  and an adder  23 - 4 . 
     The multiplier  23 - 2  multiplies the G 1 -fold detection value of the phase error fed from the multiplier  23 - 1  by a previously established loop gain G 2 . The result of the multiplication is output to an integrator  23 - 3 . The multipliers  23 - 1  and  23 - 2  serve as a multiplier block that adds the weight of the loop gain G 1  or G 2  to the input signal. 
     The integrator  23 - 3  integrates the output from the multiplier  23 - 2 , and outputs the result of the integration to the adder  23 - 4 . 
     The adder  23 - 4  adds the output from the multiplier  23 - 1  and that from the multiplier  23 - 3 . The sum of the addition is output as the result of the filtering process to the numerically controlled oscillator  24 . 
     The numerically controlled oscillator  24  generates the phase control amount e −j(2πΔft+θ)  based on the filtering result from the loop filter  23 , and outputs the generated amount to the multipliers  21  and  12 . 
     The multiplier  12  multiplies the reception signal ri by the phase control amount e −j(2πΔft+θ)  output from the numerically controlled oscillator  24 . The signal obtained through multiplication is output as a synchronized detection signal di. 
     Meanwhile, the loop gains G 1  and G 2  of the loop filter  23  determine the filtering bandwidth that characterizes the loop filter  23 . The bandwidth of the loop filter  23  and the performance of the PLL circuit  11  are known to have the following relations therebetween: 
     That is, when the loop filter has a wide (i.e., large) bandwidth, the ability to follow phase error variation is improved but the amount of the jitter in the synchronized detection signal output from the PLL is increased. Conversely, where the loop filter has a narrow (i.e., small) bandwidth, the ability to follow phase error variation is worsened but the mount of the jitter in the output synchronized detection signal is reduced. In this respect, reference may be made to Japanese Patent Laid-open No. 2009-26426. 
     SUMMARY 
     In the receiver used for actual wireless digital transmission, however, noise may occur in the phase and frequency of the reception signal due to temperature-dependent characteristics of the local oscillator or unintended oscillation inside the RF circuit. In order to realize optimum synchronization performance of the frequency/phase synchronizing circuit using the digital PLL, it may thus be required to establish optimum loop gains in keeping with the individual differences of receiver characteristics and the time jitter over transmission channels. 
     The ordinary digital PLL is capable of having only a fixed loop gain established. To obtain optimum reception performance involves setting a loop gain optimally adjusted to the reception environment for every individual receiver. Where the transmission channels are dynamically changed due to temperature and other factors so that the optimum loop gain dynamically varies accordingly, the currently used loop gain may not remain optimal. 
     Furthermore, the optimum loop gain for the PLL-based loop filter may vary depending on the modulation techniques used in the reception signal. For example, the satellite digital broadcasting scheme adopted in Japan allows a plurality of modulation techniques to coexist in a single frame. In such a case, if only one loop gain can be established, that loop gain may be optimal for a given modulation technique but not so for the other modulation techniques. This can result in worsened reception performance. 
     The present disclosure has been made in view of the above circumstances and provides a synchronizing circuit, a synchronizing method, and a receiving system capable of searching for optimum loop gains in keeping with the individual differences between receivers and the time jitter over transmission channels, even where a plurality of modulation techniques are used in a transmission frame. 
     According to one embodiment of the present disclosure, there is provided a synchronizing circuit including: a first PLL circuit configured to output, based on an input reception signal, a first phase control signal representing a phase control amount of the reception signal; a second PLL circuit configured to input the same signal as the reception signal input to the first PLL circuit so as to output a second phase control signal representing the phase control amount of the reception signal; a first output circuit configured to control the phase of the reception signal based on the first phase control signal so as to output the phase-controlled signal; a second output circuit configured to control the phase of the reception signal based on the second phase control signal so as to output the phase-controlled signal; a first detection circuit configured to detect a phase control error in the first PLL circuit based on the phase-controlled signal output from the first output circuit; a second detection circuit configured to detect a phase control error in the second PLL circuit based on the phase-controlled signal output from the second output circuit; a control circuit configured such that if the phase control error detected in the first PLL circuit by the first detection circuit is larger than the phase control error detected in the second PLL circuit by the second detection circuit, then the control circuit establishes the same value as the loop gain of a second loop filter included in the second PLL circuit as the loop gain of a first loop filter included in the first PLL circuit; and a holding section configured to hold a loop gain setting established as the loop gain of the first loop filter included in the first PLL circuit. The reception signal is structured in units of a frame made up of a plurality of slots transmitted in a plurality of transmission modes corresponding to different modulation techniques, and the holding section holds the loop gain setting for each of the transmission modes. 
     Preferably, the synchronizing circuit of the present disclosure may further include: a comparison section configured to compare in magnitude the phase control error detected in the first PLL circuit by the first detection circuit with the phase control error detected in the second PLL circuit by the second detection circuit; and a loop gain search section configured such that every time the comparison is made by the comparison section during input of the reception signal corresponding to the slots of a designated transmission mode, the loop gain search section searches for an optimum loop gain setting for the transmission mode by changing by a predetermined amount the loop gain value of the second loop filter included in the second PLL circuit. If the loop gain value of the second loop filter is changed a predetermined number of times by the loop gain search section, then the holding section may hold the value established as the loop gain of the first loop filter as the optimum loop gain setting for the transmission mode. 
     Preferably, the synchronizing circuit of the present disclosure may further include a transmission mode number identification section configured to identify a transmission mode number constituting information for identifying the transmission mode of each of the slots in the reception signal, based on control signal obtained by decoding the reception signal. If the identified transmission mode number corresponds to the designated transmission mode, then the loop gain search section may search for the optimum loop gain setting; and the holding section may hold the optimum loop gain setting in correspondence with the transmission mode number identified by the transmission mode number identification section. 
     Preferably, the first PLL circuit may include: a first detection circuit configured to detect a phase error remaining in the phase-controlled signal; the first loop filter configured to perform a filtering process on the phase error detected by the first detection circuit; a first oscillation circuit configured to output the first phase control signal depending on the result of the filtering process performed by the first loop filter; and a first output circuit configured to control the phase of the reception signal based on the first phase control signal output from the first oscillation circuit, the first output circuit further outputting the phase-controlled signal to the first detection circuit as a signal targeted for phase error detection; and the second PLL circuit may include: a second detection circuit configured to detect a phase error remaining in the phase-controlled signal; the second loop filter configured to perform a filtering process on the phase error detected by the second detection circuit; a second oscillation circuit configured to output the second phase control signal depending on the result of the filtering process performed by the second loop filter; and the second output circuit configured to control the phase of the reception signal based on the second phase control signal output from the second oscillation circuit, the second output circuit further outputting the phase-controlled signal to the second detection circuit as a signal targeted for phase error detection. 
     Preferably, the first loop filter may include: a first multiplication circuit configured to multiply the phase error detected by the first detection circuit by a first loop gain; a second multiplication circuit configured to multiply the phase error multiplied by the first multiplication circuit by a second loop gain; and a first addition circuit configured to add the phase error multiplied by the first multiplication circuit and the result of integrating the phase error multiplied by the second multiplication circuit, the first addition circuit further outputting the sum of the addition to the first oscillation circuit; and the second loop filter may include: a third multiplication circuit configured to multiply the phase error detected by the second detection circuit by third loop gain; a fourth multiplication circuit configured to multiply the phase error multiplied by the third multiplication circuit by a fourth loop gain; and a second addition circuit configured to add the phase error multiplied by the third multiplication circuit and the result of integrating the phase error multiplied by the fourth multiplication circuit, the second addition circuit further outputting the sum of the addition to the second oscillation circuit. 
     Preferably, the control circuit may establish a different value for each of the first loop gain and the third loop gain. 
     According to another embodiment of the present disclosure, there is provided a synchronizing method including: causing a first PLL circuit to output, based on an input reception signal, a first phase control signal representing a phase control amount of the reception signal; causing a second PLL circuit to input the same signal as the reception signal input to the first PLL circuit so as to output a second phase control signal representing the phase control amount of the reception signal; causing a first output circuit to control the phase of the reception signal based on the first phase control signal so as to output the phase-controlled signal; causing a second output circuit to control the phase of the reception signal based on the second phase control signal so as to output the phase-controlled signal; causing a first detection circuit to detect a phase control error in the first PLL circuit based on the phase-controlled signal output from the first output circuit; causing a second detection circuit to detect a phase control error in the second PLL circuit based on the phase-controlled signal output from the second output circuit; if the phase control error detected in the first PLL circuit by the first detection circuit is larger than the phase control error detected in the second PLL circuit by the second detection circuit, then establishing the same value as the loop gain of a second loop filter included in the second PLL circuit as the loop gain of a first loop filter included in the first PLL circuit; and holding a loop gain setting established as the loop gain of the first loop filter included in the first PLL circuit. The reception signal is structured in units of a frame made up of a plurality of slots transmitted in a plurality of transmission modes corresponding to different modulation techniques; and the loop gain setting is held for each of the transmission modes. 
     According to a further embodiment of the present disclosure, there is provided a reception system including: an acquisition section configured to acquire a signal transmitted via a transmission channel; and a transmission channel decoding process section configured to perform processing including a synchronized detection process on the signal acquired by the acquisition section. The transmission channel decoding process section includes: a first PLL circuit configured to output, based on an input reception signal, a first phase control signal representing a phase control amount of the reception signal; a second PLL circuit configured to input the same signal as the reception signal input to the first PLL circuit so as to output a second phase control signal representing the phase control amount of the reception signal; a first output circuit configured to control the phase of the reception signal based on the first phase control signal so as to output the phase-controlled signal; a second output circuit configured to control the phase of the reception signal based on the second phase control signal so as to output the phase-controlled signal; a first detection circuit configured to detect a phase control error in the first PLL circuit based on the phase-controlled signal output from the first output circuit; a second detection circuit configured to detect a phase control error in the second PLL circuit based on the phase-controlled signal output from the second output circuit; a control circuit configured such that if the phase control error detected in the first PLL circuit by the first detection circuit is larger than the phase control error detected in the second PLL circuit by the second detection circuit, then the control circuit establishes the same value as the loop gain of a second loop filter included in the second PLL circuit as the loop gain of a first loop filter included in the first PLL circuit; and a holding section configured to hold a loop gain setting established as the loop gain of the first loop filter included in the first PLL circuit. The reception signal is structured in units of a frame made up of a plurality of slots transmitted in a plurality of transmission modes corresponding to different modulation techniques, and the holding section holds the loop gain setting for each of the transmission modes. 
     According to an even further embodiment of the present invention, there is provided a receiving system including: a transmission channel decoding process section configured to perform processing including a synchronized detection process on a signal acquired via a transmission channel; and an information source decoding process section configured to decode the signal having undergone the processing performed by the transmission channel decoding process section, into data targeted for transmission. The transmission channel decoding process section includes: a first PLL circuit configured to output, based on an input reception signal, a first phase control signal representing a phase control amount of the reception signal; a second PLL circuit configured to input the same signal as the reception signal input to the first PLL circuit so as to output a second phase control signal representing the phase control amount of the reception signal; a first output circuit configured to control the phase of the reception signal based on the first phase control signal so as to output the phase-controlled signal; a second output circuit configured to control the phase of the reception signal based on the second phase control signal so as to output the phase-controlled signal; a first detection circuit configured to detect a phase control error in the first PLL circuit based on the phase-controlled signal output from the first output circuit; a second detection circuit configured to detect a phase control error in the second PLL circuit based on the phase-controlled signal output from the second output circuit; a control circuit configured such that if the phase control error detected in the first PLL circuit by the first detection circuit is larger than the phase control error detected in the second PLL circuit by the second detection circuit, then the control circuit establishes the same value as the loop gain of a second loop filter included in the second PLL circuit as the loop gain of a first loop filter included in the first PLL circuit; and a holding section configured to hold a loop gain setting established as the loop gain of the first loop filter included in the first PLL circuit. The reception signal is structured in units of a frame made up of a plurality of slots transmitted in a plurality of transmission modes corresponding to different modulation techniques, and the holding section holds the loop gain setting for each of the transmission modes. 
     According to a still further embodiment of the present disclosure, there is provided a receiving system including: a transmission channel decoding process section configured to perform processing including a synchronized detection process on a signal acquired via a transmission channel; and an output section configured to output an image and/or a sound based on the signal having undergone the processing performed by the transmission channel decoding process section. The transmission channel decoding process section includes: a first PLL circuit configured to output, based on an input reception signal, a first phase control signal representing a phase control amount of the reception signal; a second PLL circuit configured to input the same signal as the reception signal input to the first PLL circuit so as to output a second phase control signal representing the phase control amount of the reception signal; a first output circuit configured to control the phase of the reception signal based on the first phase control signal so as to output the phase-controlled signal; a second output circuit configured to control the phase of the reception signal based on the second phase control signal so as to output the phase-controlled signal; a first detection circuit configured to detect a phase control error in the first PLL circuit based on the phase-controlled signal output from the first output circuit; a second detection circuit configured to detect a phase control error in the second PLL circuit based on the phase-controlled signal output from the second output circuit; a control circuit configured such that if the phase control error detected in the first PLL circuit by the first detection circuit is larger than the phase control error detected in the second PLL circuit by the second detection circuit, then the control circuit establishes the same value as the loop gain of a second loop filter included in the second PLL circuit as the loop gain of a first loop filter included in the first PLL circuit; and a holding section configured to hold a loop gain setting established as the loop gain of the first loop filter included in the first PLL circuit. The reception signal is structured in units of a frame made up of a plurality of slots transmitted in a plurality of transmission modes corresponding to different modulation techniques, and the holding section holds the loop gain setting for each of the transmission modes. 
     According to a yet further embodiment of the present disclosure, there is provided a receiving system including: a transmission channel decoding process section configured to perform processing including a synchronized detection process on a signal acquired via a transmission channel; and a recording section configured to record the signal having undergone the processing performed by the transmission channel decoding process section. The transmission channel decoding process section includes: a first PLL circuit configured to output, based on an input reception signal, a first phase control signal representing a phase control amount of the reception signal; a second PLL circuit configured to input the same signal as the reception signal input to the first PLL circuit so as to output a second phase control signal representing the phase control amount of the reception signal; a first output circuit configured to control the phase of the reception signal based on the first phase control signal so as to output the phase-controlled signal; a second output circuit configured to control the phase of the reception signal based on the second phase control signal so as to output the phase-controlled signal; a first detection circuit configured to detect a phase control error in the first PLL circuit based on the phase-controlled signal output from the first output circuit; a second detection circuit configured to detect a phase control error in the second PLL circuit based on the phase-controlled signal output from the second output circuit; a control circuit configured such that if the phase control error detected in the first PLL circuit by the first detection circuit is larger than the phase control error detected in the second PLL circuit by the second detection circuit, then the control circuit establishes the same value as the loop gain of a second loop filter included in the second PLL circuit as the loop gain of a first loop filter included in the first PLL circuit; and a holding section configured to hold a loop gain setting established as the loop gain of the first loop filter included in the first PLL circuit. The reception signal is structured in units of a frame made up of a plurality of slots transmitted in a plurality of transmission modes corresponding to different modulation techniques, and the holding section holds the loop gain setting for each of the transmission modes. 
     Where the present disclosure is typically implemented as outlined above, the first PLL circuit is caused to output, based on an input reception signal, the first phase control signal representing the phase control amount of the reception signal; the second PLL circuit is caused to input the same signal as the reception signal input to the first PLL circuit so as to output the second phase control signal representing the phase control amount of the reception signal; the first output circuit is caused to control the phase of the reception signal based on the first phase control signal so as to output the phase-controlled signal; the second output circuit is caused to control the phase of the reception signal based on the second phase control signal so as to output the phase-controlled signal; the first detection circuit is caused to detect the phase control error in the first PLL circuit based on the phase-controlled signal output from the first output circuit; the second detection circuit is caused to detect the phase control error in the second PLL circuit based on the phase-controlled signal output from the second output circuit; if the phase control error detected in the first PLL circuit by the first detection circuit is larger than the phase control error detected in the second PLL circuit by the second detection circuit, then the same value as the loop gain of the second loop filter included in the second PLL circuit is established as the loop gain of the first loop filter included in the first PLL circuit; and the loop gain setting established as the loop gain of the first loop filter included in the first PLL circuit is held. The reception signal is structured in units of a frame made up of a plurality of slots transmitted in a plurality of transmission modes corresponding to different modulation techniques; and the loop gain setting is held for each of the transmission modes. 
     Thus according to the present disclosure, it is possible to search for optimum loop gains in keeping with the individual differences between receivers and the time jitter over transmission channels even where a plurality of modulation techniques are used in a transmission frame. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         FIG. 1  is a schematic view showing a partial structure of an ordinary receiver that includes a frequency/phase synchronizing circuit utilizing a digital PLL; 
         FIG. 2  is a schematic view showing a typical structure of a frequency/phase synchronizing circuit that uses a digital PLL and that is furnished in the setup of  FIG. 1 ; 
         FIG. 3  is a schematic view explanatory of the frame structure of the Advanced Satellite Digital Broadcasting System; 
         FIG. 4  is a schematic view showing typical transmission modes in a single frame of the Advanced Satellite Digital Broadcasting System; 
         FIG. 5  is a block diagram showing a typical structure of a frequency/phase synchronizing circuit practiced as one embodiment of the present disclosure; 
         FIG. 6  is a flowchart explanatory of a typical loop gain control process; 
         FIG. 7  is block diagram showing a typical configuration of a first embodiment of a receiving system to which the frequency/phase synchronizing circuit of the embodiments of the present disclosure is applied; 
         FIG. 8  is block diagram showing a typical configuration of a second embodiment of the receiving system to which the frequency/phase synchronizing circuit of the embodiments of the present disclosure is applied; 
         FIG. 9  is block diagram showing a typical configuration of a third embodiment of the receiving system to which the frequency/phase synchronizing circuit of the embodiments of the present disclosure is applied; and 
         FIG. 10  is a block diagram showing a typical structure of a personal computer. 
     
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     Some preferred embodiments of the present disclosure will now be described in reference to the accompanying drawings. 
     Explained first is the frame structure of the Advanced Satellite Digital Broadcasting System proposed as a next-generation satellite digital broadcasting system in Japan. 
       FIG. 3  is a schematic view explanatory of the frame structure of the Advanced Satellite Digital Broadcasting System. As illustrated, one frame is composed of 120 modulation slots. In this example, the modulation slots are numbered from # 1  to # 120 . 
     Each modulation slot includes 24 symbols for synchronization purposes (indicated as “Fsync,” “!Fsync” and “Ssync” in  FIG. 3 ) and 32 known symbols (each indicated as “Pilot” in  FIG. 3 ) used for determining signal constellation points. 
     Also, each modulation slot includes 66 transmitted data items each composed of 136 symbols. For example, the transmitted data items in modulation slot # 1  are indicated as “Data # 1 ” through “Data # 66 ,” and the transmitted data items in modulation slot # 2  are shown as “Data # 67 ” through “Data # 132 .” 
     Furthermore, in each modulation slot, a TMCC signal is inserted between every two transmitted data items, the signal being made up of four symbols constituting control information about transmission and multiplexing. In  FIG. 3 , reference character T denotes the TMCC signal. 
     Each frame of the Advanced Satellite Digital Broadcasting System structured as explained above is made up of a total of 1,115,520 symbols. 
     The Advanced Satellite Digital Broadcasting System makes it possible for a plurality of modulation techniques to coexist in each frame. For example, up to eight transmission modes may be defined in a single frame, each transmission mode allowing a different modulation technique to be adopted. With the Advanced Satellite Digital Broadcasting System, it is possible to use five modulation techniques consisting of BPSK, QPSK, 8PSK, 16APSK, and 32APSK. 
       FIG. 4  is a schematic view showing typical transmission modes in a single frame of the Advanced Satellite Digital Broadcasting System. For purpose of simplification, only two transmission modes are defined. As shown in  FIG. 4 , transmission mode  1  set for the transmission technique of 32APSK is assigned to modulation slots # 1  through # 40 , and transmission mode  2  for the transmission technique of 16APSK is assigned to modulation slots # 41  through # 120 . 
     The transmission mode of each modulation slot can be identified by analyzing the TMCC signal found two frames earlier than the current frame. The receiver is thus arranged to acquire and retain all TMCC signals inserted in each modulation slot of the frame received two frames earlier. This arrangement allows the receiver to identify the modulation technique for each modulation slot in each frame received. Regardless of the transmission mode of each modulation slot, it should be noted, the TMCC signal is typically subjected to π/2 shift BPSK modulation. 
     The present disclosure aims to search for optimum loop gains even where a plurality of modulation techniques are used in each transmission frame, as shown in  FIG. 4  for example. 
       FIG. 5  is a block diagram showing a typical structure of a frequency/phase synchronizing circuit practiced as one embodiment of the present disclosure. 
     The frequency/phase synchronizing circuit shown in  FIG. 5  is incorporated in the demodulation circuit  3  of a receiver having the same structure as that indicated in  FIG. 1 . 
     The structure of the frequency/phase synchronizing circuit shown in  FIG. 5  is largely different from the ordinary circuit structure in the following: that a main PLL circuit is supplemented with a sub PLL circuit having the same structure, that the loop gains of the loop filters in the main and sub PLL circuits are variable, and that a loop gain control setup is additionally provided. 
     The main PLL circuit  31 - 1  and the sub PLL circuit  31 - 2  are structured in such a manner as to use members that have the same characteristics and to possess the same circuit structure. If the same value is set as the loop gain of the loop filter in each of the main and sub PLL circuits  31 - 1  and  31 - 2  and if the same signal is input to the two circuits, then the signal output from the main PLL circuit  31 - 1  coincides with the signal output from the sub PLL circuit  31 - 2 . 
     As will be explained later, the main PLL circuit  31 - 1  is a circuit that actually performs synchronized detection. The sub PLL circuit  31 - 2  may be considered a circuit that performs “trials” to determine the loop gain defining the characteristics of the loop filter in the main PLL circuit  31 - 1 . 
     The reception signal ri, which is the i-th signal (at the i-th symbol), is input to a multiplier  41 - 1  of the main PLL circuit  31 - 1 , to a multiplier  41 - 2  of the sub PLL circuit  31 - 2 , and to a multiplier  32 . The reception signal ri includes the phase error represented by 2πΔft+θ as mentioned above. 
     The multiplier  41 - 1  of the main PLL circuit  31 - 1  multiplies the reception signal ri by a phase control amount e −j(2πΔft+θ)  supplied from a numerically controlled oscillator  44 - 1 . A signal d main,i  obtained through multiplication is output to a phase error detector  42 - 1 . The signal output from the multiplier  41 - 1  is the same as a synchronized detection signal d main,i  that is a phase control signal output from the multiplier  32 . 
     The phase error detector  42 - 1  detects a phase error that may remain in the signal output from the multiplier  41 - 1 , and outputs a main phase error detection value e main,i . The phase error detector  42 - 1  performs phase error detection in the same manner as the phase error detector  22  shown in  FIG. 2 . The same holds for a phase error detector  42 - 2  of the sub PLL circuit  31 - 2 , to be discussed later. 
     The main phase error detection value e main,i  output from the phase error detector  42 - 1  is fed to a multiplier  51 - 1  of a loop filter  43 - 1 . 
     The loop filter  43 - 1  is a proportional integral loop filter that filters the main phase error detection value e main,i  output from the phase error detector  42 - 1 . The filtered value is output to the numerically controlled oscillator  44 - 1 . 
     More specifically, the multiplier  51 - 1  of the loop filter  43 - 1  multiplies the main phase error detection value e main,i  by G 1   main  in accordance with a loop gain G 1   main  established by a loop gain control portion  34 . The value obtained through multiplication is output to a multiplier  52 - 1  and an adder  54 - 1 . 
     The multiplier  52 - 1  further multiplies by G 2  the G 1   main -fold main phase error detection value e main,i  fed from the multiplier  51 - 1 . The value obtained through multiplication is output to an integrator  53 - 1 . 
     The integrator  53 - 1  integrates the output from the multiplier  52 - 1  and outputs the result of the integration to the adder  54 - 1 . 
     The adder  54 - 1  adds the output from the multiplier  51 - 1  and the output from the integrator  53 - 1 , and outputs the sum of the addition as a filtering result θ main,i  to the numerically controlled oscillator  44 - 1 . 
     The numerically controlled oscillator  44 - 1  generates the phase control amount e −j(2πΔft+θ)  based on the filtering result from the loop filter  43 - 1 , and outputs the generated control amount to the multipliers  41 - 1  and  32 . 
     The multiplier  32  multiplies the reception signal ri by the phase control amount e −j(2πΔft+θ)  supplied from the numerically controlled oscillator  44 - 1  of the main PLL circuit  31 - 1 . The signal obtained through multiplication is output as the synchronized detection signal d main,i . 
     Meanwhile, a signal containing the signal d main,i , main phase error detection value e main,i , and filtering result θ main,i  is supplied from the main PLL circuit  31 - 1  as a main PLL intermediate signal to a main PLL control error detector  61  of a PLL control error comparison portion  33 . 
     The sub PLL circuit  31 - 2  also performs the same processing on the same reception signal ri as that input to the main PLL circuit  31 - 1 . 
     That is, the multiplier  41 - 2  of the sub PLL circuit  31 - 2  multiplies the reception signal ri by the phase control amount e −j(2πΔft+θ)  supplied from a numerically controlled oscillator  44 - 2 . A signal d sub,i  obtained through multiplication is output to a phase error detector  42 - 2 . 
     The phase error detector  42 - 2  detects a phase error that may remain in the signal output from the multiplier  41 - 2 , and outputs a sub phase error detection value e sub,i  accordingly. The sub phase error detection value e sub,i  output from the phase error detector  42 - 2  is fed to a multiplier  51 - 2  of a loop filter  43 - 2 . 
     The multiplier  51 - 2  of the loop filter  43 - 2  multiplies the sub phase error detection value e sub,i  by G 1   sub  in accordance with a loop gain G 1   sub  established by the loop gain control portion  34 . The value obtained through multiplication is output to a multiplier  52 - 2  and an adder  54 - 2 . 
     For example, the loop gain G 1   sub  set for the multiplier  51 - 2  is made different from the loop gain G 1   main  set for the multiplier  51 - 1  of the main PLL circuit  31 - 1 . 
     The multiplier  52 - 2  further multiplies by G 2  the G 1   sub -fold sub phase error detection value e sub,i  fed from the multiplier  51 - 2 . The value obtained through multiplication is output to an integrator  53 - 2 . The multiplier  52 - 1  of the main PLL  31 - 1  and the multiplier  52 - 2  of the sub PLL circuit  31 - 2  thus perform weighting by use of the same loop gain. The loop gain G 2  is a predetermined fixed value. 
     The integrator  53 - 2  integrates the output from the multiplier  52 - 2  and outputs the result of the integration to the adder  54 - 2 . 
     The adder  54 - 2  adds the output from the multiplier  51 - 2  and the output from the integrator  53 - 2 , and outputs the sum of the addition as a filtering result θ sub,i  to the numerically controlled oscillator  44 - 2 . 
     The numerically controlled oscillator  44 - 2  generates the phase control amount e −j(2πΔft+θ)  based on the filtering result from the loop filter  43 - 2 , and outputs the generated control amount to the multiplier  41 - 2 . 
     Meanwhile, a signal containing the signal d main,i , sub phase error detection value e sub,i , and filtering result θ sub,i  is supplied from the sub PLL circuit  31 - 2  as a sub PLL intermediate signal to a sub PLL control error detector  62  of the PLL control error comparison portion  33 . 
     The main PLL control error detector  61  of the PLL control error comparison portion  33  receives the main PLL intermediate signal fed from the main PLL circuit  31 - 1  every time the reception signal ri is input. For example, the main PLL control error detector  61  calculates a variance value of the main phase error detection value e main,i  obtained out of the reception signal ri having a predetermined number of symbols. The variance value thus acquired is output to a comparator  63  as a control error value v main . 
     The control error value v main  is calculated based on the result of the multiplication performed by the multiplier  41 - 1 , i.e., on the main phase error detection value e main,i  representing the detected phase error remaining in the signal having undergone the phase control by the main PLL circuit  31 - 1 . For that reason, the control error value v main  denotes the error of the phase control carried out by the main PLL circuit  31 - 1 . 
     The sub PLL control error detector  62  receives the sub PLL intermediate signal fed from the sub PLL circuit  31 - 2  every time the reception signal ri is input. For example, the sub PLL control error detector  62  calculates a variance value of the sub phase error detection value e sub,i  obtained out of the reception signal ri having a predetermined number of symbols. The variance value thus acquired is output to the comparator  63  as a control error value v sub . 
     The control error value v sub  is calculated based on the result of the multiplication performed by the multiplier  41 - 2 , i.e., on the sub phase error detection value e sub,i  representing the detected phase error remaining in the signal having undergone the phase control by the sub PLL circuit  31 - 2 . For that reason, the control error value v sub  denotes the error of the phase control carried out by the sub PLL circuit  31 - 2 . 
     The comparator  63  compares in magnitude the control error value v main  supplied from the main PLL control error detector  61  with the control error value v sub  fed from the sub PLL control error detector  62 . The result of the comparison is output to the loop gain control portion  34  in response to a comparison result output notification supplied from a timer  64 . 
     As described, the loop filter  43 - 1  of the main PLL circuit  31 - 1  and the loop filter  43 - 2  of the sub PLL circuit  31 - 2  use the different loop gains G 1   main  and G 1   sub . It follows that a difference reflecting the discrepancy between the loop gains G 1   main  and G 1   sub  appears in the control error value v main  calculated by the main PLL control error detector  61  and in the control error value v sub  computed by the sub PLL control error detector  62 . 
     The foregoing paragraphs discussed an example in which the control error values v main  and v sub  are calculated based on the main and sub phase error detection values e main,i  and e sub,i . Alternatively, the control error values v main  and v sub  may be computed based on the signal d main,i ; on the filtering result θ main,i  and signal d sub,i ; or on the filtering result θ sub,i . 
     The timer  64  starts counting time upon receipt of an initialization flag fed from the loop gain control portion  34 . Upon elapse of a predetermined count time, the timer  64  outputs a comparison complete notification to the loop gain control portion  34 . The time it takes to calculate the control error value is preset on the timer  64 , and the preset time is counted by the timer  64 . The timer  64  also outputs a comparison result output notification to the comparator  63  simultaneously with outputting the comparison complete notification to the loop gain control portion  34 . 
     The loop gain control portion  34  has a gain control sequencer  72  furnished inside. The loop gain control portion  34  searches for optimum loop gains while monitoring the operation status of the main and sub PLL circuits  31 - 1  and  31 - 2 , and establishes the detected optimum loop gains for their respective loop filters. 
     For example, if the control error value v main  calculated by the main PLL control error detector  61  is larger than the control error value v sub  computed by the sub PLL control error detector  62 , the loop gain control portion  34  sets the same value as the loop gain G 1   sub  to the loop filter  43 - 1  of the main PLL circuit  31 - 1 , replacing the previously established loop gain G 1   main . 
     That the control error value v main  is larger than the control error value v sub  signifies that synchronous acquisition can be performed with less error by establishing the loop gain G 1   sub  set to the loop filter  43 - 2  of the sub PLL circuit  31 - 2 . Thus in this case, the loop gain G 1   main  for the loop filter  43 - 1  of the main PLL circuit  31 - 1  is replaced by the loop gain G 1   sub . 
     If the control error value v sub  calculated by the sub PLL control error detector  62  is larger than the control error value v main  computed by the main PLL control error detector  61 , the gain control sequencer  72  of the loop gain control portion  34  leaves the loop gain G 1   main  unchanged for the loop filter  43 - 1  of the main PLL circuit  31 - 1 . 
     That the control error value v sub  is larger than the control error value v main  as described above signifies that using the loop gain G 1   main  unchanged allows synchronous acquisition to be performed with less error than if the loop gain G 1   sub  is utilized. Thus in this case, the loop gain G 1   main  for the loop filter  43 - 1  of the main PLL circuit  31 - 1  will not be replaced by the loop gain G 1   sub . 
     As described, after it has been determined whether or not to replace the loop gain G 1   main , the loop gain G 1   sub  for the loop filter  43 - 2  is changed. Then another comparison is made in magnitude between the control error value v sub  and the control error value v main  so as to determine whether or not to replace the loop gain G 1   main . In this manner, searches continue for the optimum loop gains. 
     When the loop gain G 1   sub  is to be changed, the gain control sequencer  72  establishes the loop gain G 1   sub  using the formula of G 1   sub =G 1   sub +α, where α stands for the smallest step of the established G 1  being quantized. In this case, if the established G 1   sub  exceeds a maximum tolerable value G 1   max , the loop gain control portion  34  outputs a search complete signal. 
     The loop gain control portion  34  causes an internally furnished transmission mode-specific gain selection portion  71  to hold the loop gain G 1   main  for each of the transmission modes involved for selective loop gain output. For this reason, the transmission mode-specific gain selection portion  71  possesses as many registers as the maximum number N of the transmission modes involved (e.g., N=8), each register being used to hold an optimum loop gain for the transmission mode in question. It is assumed that these registers give output values G 1 main0, G 1 main1, . . . G 1 mainN−1. 
     The transmission mode of the reception signal ri, the modulation technique adopted for each transmission mode, and the modulation slots assigned to the transmission mode in question are identified by the TMCC fed from an error correction decoder  91 . 
     A transmission mode number generator  92  counts the received symbols starting from an input frame start flag and, based on the received symbol count value, identifies which modulation slot the currently received symbol belongs to. Also, based on information acquired from the TMCC signal and representing the modulation slots assigned to each transmission mode, the transmission mode number generator  92  determines the number TM identifying the transmission mode of the currently received symbol (TM is called the transmission mode number) and outputs the transmission mode number TM to the loop gain control portion  34 . 
     For example, if the currently received transmission scheme has as many as “n” transmission modes multiplexed therein, then the transmission mode numbers TM are 0, 1, . . . n−1. 
     The gain control sequencer  72  holds a transmission mode number TMtarget about which a search for an optimum loop gain is to be made. Only during reception of the symbols for which TM=TMtarget, does the gain control sequencer  72  allow the PLL control error comparator  33  and transmission mode-specific gain selection portion  71  to operate. The gain control sequencer  72  outputs an update EN (enable) signal that goes High during reception of the symbols for which TM=TMtarget, to the PLL control error comparison portion  33  and transmission mode-specific gain selection portion  71 . 
     While the update EN signal is being High, the PLL control error comparison portion  33  carries out the processes discussed above. Where the loop gain G 1   main  is to be replaced by the loop gain G 1   sub  while the update EN signal is being High, an update flag generation portion inside the transmission mode-specific gain selection portion  71  outputs a flag for writing to a loop gain register corresponding to the transmission mode number TM currently in effect. 
     When the frequency/phase synchronizing circuit shown in  FIG. 5  is started, the transmission mode number about which a search for the optimum loop gain is to be made is initialized (TMtarget=0). Then the loop gains for the main and sub PLL circuits  31 - 1  and  31 - 2  are initialized. 
     After the loop gains for the main and sub PLL circuits  31 - 1  and  31 - 2  have been initialized, the loop gain control portion  34  outputs an initialization flag to the PLL control error comparison portion  33 . 
     Upon receipt of the initialization flag from the loop gain control portion  34 , the PLL control error comparison portion  33  resets the currently effective result of the control error value comparison as well as the timer  64 . Thereafter, the PLL control error comparison portion  33  calculates the control error value v main,i  and v sub,i  as discussed above. The comparator  63  starts comparing these control error values in magnitude. 
     Upon being reset, the timer  64  of the PLL control error comparison portion  33  starts counting time. When the count time necessary for calculating the control error value is reached, the timer  64  outputs a comparison complete notification to the loop gain control portion  34 . At the same time, the timer  64  outputs a comparison result output command to the comparator  63 . This in turn causes the comparator  63  to output the result of the control error comparison to the loop gain control portion  34 . 
     Given the control error comparison result, the loop gain control portion  34  controls accordingly the loop gains to be supplied to the loop filters  43 - 1  and  43 - 2 . At this point, if the loop gain G 1   main  is to be replaced by the loop gain G 1   sub , the gain control sequencer  72  feeds the loop gain G 1   sub  to the transmission mode-specific gain selection portion  71  as discussed above. 
     The transmission mode-specific gain selection portion  71  updates the value held in a loop gain register G 1 main[TM], one of a plurality of internal registers which corresponds to the transmission mode number TM, by use of the value input from the gain control sequencer  72 . 
     Also, the transmission mode-specific gain selection portion  71  selects from G 1 main0, G 1 main1, . . . G 1 mainN−1 the loop gain corresponding to the transmission mode number TM fed from the transmission mode number generator  92 , and outputs the selected loop gain as the loop gain for the loop filter  43 - 1 . 
     If a search complete signal is output from the gain control sequencer  72  before a comparison complete notification is received from the PLL control error comparison portion  33 , then a check is made to see if the TMtarget value equals n−1 so as to determine whether the search for the optimum gains for all transmission modes has been completed. If the TMtarget value is not equal to n−1, then the TMtarget value is incremented by 1 in order to make a search for the optimum gain for the next transmission mode. At the same time, the loop gains for the main and sub PLL circuits  31 - 1  and  31 - 2  are again initialized. 
     In the manner described above, the search is made for the optimum loop gain regarding each of the TMtarget values 0 through n−1. This makes it possible to establish the optimum loop gain for each of the transmission modes involved based on different modulation techniques. 
     Alternatively, if a search complete signal is output from the gain control sequencer  72  before a comparison complete notification is received from the PLL control error comparison portion  33  and if the TMtarget value is equal to n−1, then the TMtarget value may be reset to 0. That is, after the search has been made for the optimum loop gain regarding each of the TMtarget values 0 through n−1, another search may again be started for an optimum loop gain regarding each of the TMtarget values 0 through n−1. 
     In this manner, even where there exists time jitter in the transmission characteristics of the transmission channels involved, searches for optimum loop gains can be made continuously and the detected loop gains may be used uninterruptedly. 
     Explained below in reference to the flowchart of  FIG. 6  is a typical loop gain control process performed by the frequency/phase synchronizing circuit shown in  FIG. 5 . 
     In step S 11 , the gain control sequencer  72  initializes the variable TMtarget to 0. 
     In step S 12 , the gain control sequencer  72  initializes that loop gain register inside the transmission mode-specific gain selection portion  71  which corresponds to the variable TMtarget. In this example, the setting of the loop gain register in question is represented by G 1   main     —     new  and the initial value thereof by G 1   init . The setting G 1   main     —     new  is used as the loop gain G 1   main  for the loop filter  43 - 1 . 
     Also in step S 12 , the gain control sequencer  72  initializes the loop gain G 1   sub  for the loop filter  43 - 2 . The initial value of the loop gain G 1   sub  is the smallest loop gain that is G 1   min . The setting G 1   sub  is used as the loop gain G 1   sub  for the loop filter  43 - 2 . 
     Step S 13  is reached following the loop gain initialization. In step S 13 , the loop gain control portion  34  outputs an initialization flag to the PLL control error comparison portion  33 . 
     Upon receipt of the initialization flag, the PLL control error comparison portion  33  resets the result of the control error comparison carried out so far as well as the count value on the internal timer. 
     Also, the main PLL control error detector  61  of the PLL control error comparison portion  33  calculates the control error value v main  based on the main PLL intermediate signal output from the main PLL circuit  31 - 1 . The sub PLL control error detector  62  computes the control error value v sub  based on the sub PLL intermediate signal output from the sub PLL circuit  31 - 2 . 
     After being reset, the timer  64  starts counting time. Upon elapse of a predetermined count time necessary for calculating the control error values v main  and v sub , the timer  64  outputs a comparison complete notification to the loop gain control portion  34 . At the same time, the timer  64  outputs a comparison result output command to the comparator  63 . In response to the comparison result output command, the comparator  63  outputs the result of the comparison in magnitude between the control error values v main  and v sub  to the loop gain control portion  34 . 
     In step S 14 , the gain control sequencer  72  determines whether the comparison complete notification output from the timer  64  is detected. If it is determined that the comparison complete notification is not detected yet, control is passed on to step S 20 . 
     In step S 20 , it is determined whether a search complete signal is output. If it is determined that the search complete signal is not output yet, control is passed on to step S 21 . In step S 21 , the comparison complete notification from the timer  64  is polled at intervals of a predetermined time period in a wait state. Thereafter, control is returned to step S 14 . 
     If it is determined in step S 14  that the comparison complete notification is detected, control is passed on to step S 15 . 
     In step S 15 , the gain control sequencer  72  determines whether v main &gt;v sub  based on the comparison result fed from the comparator  63 . 
     If it is determined in step S 15  that v main &gt;v sub  then step S 16  is reached. In step S 16 , the gain control sequencer  72  replaces the loop gain G 1   main     —     new  with G 1   sub  currently established as the loop gain for the loop filter  43 - 2 . At this point, the gain control sequencer  72  outputs a predetermined signal to the update flag generation portion inside the transmission mode-specific gain selection portion  71 . In turn, the update flag generation portion outputs a flag for writing to the loop gain register corresponding to the transmission mode number TM currently in effect. 
     If it is determined in step S 15  that v main ≦v sub  instead of v main &gt;v sub , then step S 16  is skipped. 
     In step S 17 , the gain control sequencer  72  establishes G 1   sub +α and updates the loop gain G 1   sub  therewith, where a denotes the amount of gain corresponding to the smallest step of the loop gain G 1  (G 1   main  or G 1   sub ) being quantized. 
     In step S 18 , the gain control sequencer  72  determines whether the loop gain G 1   sub  updated in step S 17  exceeds the maximum tolerable value G 1   max . 
     If it is determined in step S 18  that the loop gain G 1   sub  has exceeded the maximum value G 1   max , control is passed on to step S 19 . In step S 19 , the gain control sequencer  72  outputs a search complete signal. 
     If it is determined in step S 18  that the loop gain G 1   sub  has not exceeded the maximum value G 1   max , then step S 19  is skipped. 
     Control is returned to step S 13  if it is determined in step S 18  that the loop gain G 1   sub  has not exceeded the maximum value G 1   max , or after step S 19  has been completed. 
     After the search complete signal is output in step S 19 , the signal output is confirmed in step S 20 . Thereafter, control is returned to step S 22 . 
     In step S 22 , the gain control sequencer  72  determines whether the variable TMtarget is equal to n−1. If it is determined that the variable TMtarget is not equal to n−1, control is passed on to step S 23 . In step S 23 , the gain control sequencer  72  increments the variable TMtarget by 1. Control is then returned to step S 12 . That is, another search is made here for the optimum loop gain for the next transmission mode number. 
     If it is determined in step S 22  that the variable TMtarget is equal to n−1, control is returned to step S 11 . That is, after the search has been made for the optimum loop gains for all transmission mode numbers, a second search is started for the optimum loop gain for each of the TMtarget values 0 through n−1. In the second and subsequent searches, there is no need to initialize G 1   main     —     new  in step S 12 . 
     Alternatively, if it is determined in step S 22  that the variable TMtarget is equal to n−1, the loop gain control process may be terminated. 
     The loop gain control process is carried out in the manner described above. Thus according to the present disclosure, it is possible to search for optimum loop gains in keeping with the individual differences between receivers and the time jitter over transmission channels even where a plurality of modulation techniques are used in the transmission frame. 
     The foregoing paragraphs have explained examples in which the search is made for the optimum loop gain as the loop gain G 1  for use in direct multiplications performed on the detected phase error in the frequency/phase synchronizing circuit. Alternatively, a search may be made for the loop gain G 2  for use in the multiplication to be performed on the phase error resulting from the multiplication using the loop gain G 1 . 
     As another alternative, searches may be made for both the loop gain G 1  and the loop gain G 2 . 
       FIG. 7  is block diagram showing a typical configuration of a first embodiment of a receiving system to which the frequency/phase synchronizing circuit of the embodiments of the present disclosure is applied. 
     The receiving system of  FIG. 7  is made up of an acquisition portion  101 , a transmission channel decoding process portion  102 , and an information source decoding process portion  103 . 
     The acquisition portion  101  acquires a signal via transmission channels such as terrestrial digital broadcasts, satellite digital broadcasts, CATV networks and the Internet, not shown, and forwards the acquired signal to the transmission channel decoding process portion  102 . 
     Given the signal acquired by the acquisition portion  101  via the transmission channels, the transmission channel decoding process portion  102  performs a transmission channel decoding process including synchronized detection and error correction on the received signal, and forwards the signal resulting from the decoding process to the information source decoding process portion  103 . That is, the transmission channel decoding process  102  includes the structure of the frequency/phase synchronizing circuit shown in  FIG. 5  that performs the above-mentioned synchronized detection. 
     The information source decoding process portion  103  performs an information source decoding process on the signal having undergone the transmission channel decoding process, the information source decoding process including the process of expanding the compressed information back to the original information whereby the transmitted data is acquired. 
     That is, the signal acquired by the acquisition portion  101  via the transmission channels may have undergone compression coding whereby the original information was compressed so as to reduce the amount of the data such as video and audio data. In such a case, the information source decoding process portion  103  performs the information source decoding process on the signal having undergone the transmission channel decoding process, the information source decoding process including the process of expanding the compressed information back to the original information. 
     If the signal acquired by the acquisition portion  101  via the transmission channels has not undergone compression coding, the information source decoding process portion  103  does not perform the process of expanding the compressed information back to the original information. The expanding process includes MPEG decoding, for example. The information source decoding process may include descrambling in addition to the expanding process. 
     The receiving system of  FIG. 7  may be applied to TV tuners for receiving digital TV broadcasts, for example. The acquisition portion  101 , transmission channel decoding processing portion  102 , and information source decoding processing portion  103  may each be implemented in the form of an independent device (hardware (e.g., IC (integrated circuit)) or a software module). 
     Alternatively, the acquisition portion  101 , transmission channel decoding processing portion  102 , and information source decoding processing portion  103  may be implemented altogether as an independent device. As another alternative, the acquisition portion  101  and transmission channel decoding processing portion  102  may be implemented in combination as an independent device. As a further alternative, the transmission channel decoding processing portion  102  and information source decoding processing portion  103  may be implemented in combination as an independent device. 
       FIG. 8  is block diagram showing a typical configuration of a second embodiment of the receiving system to which the frequency/phase synchronizing circuit of the embodiments of the present disclosure is applied. 
     Of the components in  FIG. 8 , those with their corresponding counterparts shown in  FIG. 7  are designated by like reference numerals, and their explanations may be omitted where appropriate. 
     The configuration of the receiving system in  FIG. 8  is common to the configuration of its counterpart in  FIG. 7  in that the acquisition portion  101 , transmission channel decoding process portion  102 , and information source decoding process portion  103  are provided. On the other hand, the configuration of  FIG. 8  is different from that of  FIG. 7  in that an output portion  111  is additionally provided. 
     The output portion  111  may be typically composed of a display device for displaying images and of speakers for outputting sounds. As such, the output portion  111  outputs images and sounds derived from the signal output from the information source decoding process portion  103 . In short, the output portion  111  is a component that outputs images and/or sounds. 
     The receiving system of  FIG. 8  may be applied to TV sets for receiving digital TV broadcasts and to radio receivers for receiving radio broadcasts, for example. 
     If the signal acquired by the acquisition portion  101  has not undergone compression coding, then the signal output from the transmission channel decoding process portion  102  is fed directly to the output portion  111 . 
       FIG. 9  is block diagram showing a typical configuration of a third embodiment of the receiving system to which the frequency/phase synchronizing circuit of the embodiments of the present disclosure is applied. 
     Of the components in  FIG. 9 , those with their corresponding counterparts shown in  FIG. 7  are designated by like reference numerals, and their explanations may be omitted where appropriate. 
     The configuration of the receiving system in  FIG. 9  is common to the configuration of its counterpart in  FIG. 7  in that the acquisition portion  101  and transmission channel decoding process portion  102  are provided. On the other hand, the configuration of  FIG. 9  is different from that of  FIG. 7  in that the information source decoding process portion  103  is not provided and a recording portion  121  is additionally furnished. 
     The recording portion  121  records (stores) the signal (e.g., TS packets in the MPEG format) output from the transmission channel decoding process portion  102  to recording (storage) media such as optical disks, hard disks (magnetic disks), and flash memories. 
     The above-described receiving system of  FIG. 9  may be applied to recorders for recording TV broadcasts, for example. 
     As another example, the receiving system of  FIG. 9  may be furnished with the information source decoding process portion  103 . In this case, the recording portion  121  may record the signal having undergone the information source decoding process performed by the information source decoding process portion  103 , i.e., images and sounds acquired through the decoding process. 
     The series of processes described above may be executed either by hardware or by software. Where the software-based processing is to be carried out, the programs constituting the software may be either incorporated beforehand in the dedicated hardware of the computer to be used, or installed upon use over a network or from a suitable recording medium into a general-purpose personal computer or like equipment such as a personal computer  700  shown in  FIG. 10  capable of executing diverse functions based on the installed programs. 
     In  FIG. 10 , a CPU (central processing unit)  701  performs various processes in accordance with the programs stored in a ROM (read only memory)  702  or according to the programs loaded from a storage device  708  into a RAM (random access memory)  703 . The RAM  703  may also accommodate data and other resources needed by the CPU  701  in carrying out diverse processing. 
     The CPU  701 , ROM  702 , and RAM  703  are interconnected via a bus  704 . An input/output interface  705  is also connected to the bus  704 . 
     The input/output interface  705  is connected with an input device  706 , output device  707 , storage device  708 , and communication device  709 . The input device  706  is generally composed of a keyboard and a mouse. The output device  70  is usually constituted by a display unit such as LCD (liquid crystal display) and speakers. The storage device  708  is typically formed by a hard disk. The communication device  709  is ordinarily structured with a modem and a network interface such as a LAN card. The communication device  709  conducts communications over networks including the Internet. 
     A drive  710  may be further connected as needed to the input/output interface  705 . A piece of removable media  711  such as magnetic disks, optical disks, magneto-optical disks or semiconductor memories may be loaded into the drive  710 . Computer programs may be retrieved from the loaded removable medium and installed as needed into the storage device  708 . 
     Where the above-described series of processes is to be executed by software, the programs making up the software may be installed over networks including the Internet or from recording media such as the removable media  711 . 
     As shown in  FIG. 10 , the recording media which are offered to users apart from their computers and which accommodate the programs may be constituted not only by the removable media  711  such as magnetic disks (including floppy disks (registered trademark)), optical disks (including CD-ROM (compact disk read-only memory) and DVD (digital versatile disk)), magneto-optical disks (including MD (Mini-disk; registered trademark)), or semiconductor memories; but also by such recording media as the ROM  702  or hard disks contained in the storage device  708 . The latter recording media with the programs stored thereon are preinstalled in the computer when offered to the user. 
     In this specification, the series of the processes discussed above include not only the processes carried out in the depicted sequence (i.e., on a time series basis) but also processes that may be conducted parallelly or individually and not necessarily chronologically. 
     It should be understood by those skilled in the art that various modifications, combinations, sub-combinations and alterations may occur depending on design requirements and other factors in so far as they are within the scope of the appended claims or the equivalents thereof. 
     The present disclosure contains subject matter related to that disclosed in Japanese Priority Patent Application JP 2010-219644 filed in the Japan Patent Office on Sep. 29, 2010, the entire content of which is hereby incorporated by reference.

Technology Category: 5