Patent Document

BACKGROUND OF THE INVENTION 
     1. Field of the Invention 
     This invention relates generally to loop acquisition and, more particularly, to a system and method for determining the frequency tolerance of a synthesized signal without a frequency reference source. 
     2. Description of the Related Art 
     The use of oscillators and synthesized frequency sources are well known in communications. These frequencies are used in the generation of carrier signal and local oscillator signals, or used in the modulation and demodulation of information. The frequency tolerance of these signals is critical, and communications are degraded when the synthesized signal is out of tolerance. Conventionally, a frequency source, such as a crystal, that is highly stable with respect to temperature, initial calibration, and aging is used in the generation of the signals. Often the reference signal is baseband and must be translated up in frequency for use in the communication circuitry. 
     However, there are problems with the use of reference frequency circuits. The reference circuits use valuable board real estate and consume power, that may be critical in portable or battery operated equipment. Further, the parts can be expensive, with a premium paid for increased accuracy. In some applications the reference circuitry must be warmed up. If the warm up time is significant, a significant amount of data can be lost before the required frequency accuracy is obtained. Further, the additional parts count of the reference circuit increases the probability of circuit failure. 
     In some applications, the communication carrier frequency or modulation frequency may be variable, so the reference circuit must provide a plurality of reference frequencies. Thus, additional crystals may be required, or selectable loop dividers. 
     A so-called Bang-Bang phase detector can be used to acquire an input data signal without the need of a reference signal. However, the Bang-Bang phase detector cannot control the oscillator frequency with a fine degree of resolution. For example, it is difficult to use a Bang-Bang phase detector to control an oscillator sufficiently to meet synchronous optical network (SONET) standards. The accuracy of the oscillator remains uncertain unless a frequency reference is used. 
     It would be advantageous if accurate oscillator or clock frequencies could be generated without a reference frequency. 
     It would be advantageous if the oscillator frequency needed to receive communications could be derived from the received carrier signal or data signal. 
     SUMMARY OF THE INVENTION 
     Accordingly, the invention provides a system and method for determining when the oscillator or voltage controlled oscillator (VCO) clock frequency and the input date rate are within a specified frequency tolerance, without the use of a reference clock. 
     The method comprises: measuring the frequency of an oscillator signal; measuring the difference between the oscillator signal frequency and a data signal rate; reinitializing the measurement of the oscillator signal frequency in response to the frequency difference beatnote, or reset signal, between the oscillator and data signals; and, determining a sufficient tolerance (lock) between the oscillator frequency and data signal rate, in response to completing the measurement of the oscillator signal frequency. 
     More specifically, the oscillator frequency is measured by counting cycles of the oscillator signal, and a lock is determined between the oscillator signal frequency and data signal rate by counting a predetermined first number of cycles without an intervening beatnote occurrence. When a beatnote occurs, the count of the oscillator signal cycles is reinitialized. 
     Once lock is determined, the method further comprises: determining an insufficient tolerance (loss of lock) between the oscillator signal frequency and the data signal rate in response to generating reset signals. However, for reasons of hysteresis, at least a predetermined second number of consecutive reset signals must be counted, without an intervening count of the first number of oscillator cycles. That is, without an intervening first number count. 
     Additional details of the frequency tolerance determination method, and a system for determining frequency tolerance without the use of a reference frequency are presented below. 
    
    
     BRIEF DESCRIPTION OF THE DRAWING 
     FIG. 1 illustrates the present invention system for determining frequency tolerance; 
     FIG. 2 is a more detailed depiction of the beatnote regulator of FIG. 1; 
     FIG. 3 is a more detailed depiction of the lock analyzer of FIG. 1; 
     FIG. 4 is a schematic block diagram illustrating an exemplary use of the system of FIG. 1; and 
     FIGS. ( 5   a ,  5   b ) is a flowchart illustrating the present invention method for determining frequency tolerance. 
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     FIG. 1 illustrates the present invention system for determining frequency tolerance. The system  100  comprises a beatnote regulator  102  having a first input on line  104  to accept a beatnote signal. The beatnote signal has a frequency equal to the difference between input frequencies. For example, between an oscillator signal frequency and a data signal rate. The beatnote regulator has an output on line  106  to provide a reset signal in response to the beatnote signal. 
     A counter  108  has a first input to accept and count cycles of the oscillator signal on line  110 . The counter  108  has an output on line  112  to provide an overflow signal, or most significant bit (MSB) in response to meeting a first count. The counter has a second input connected to the beatnote regulator output on line  106  to reinitialize the count. 
     A lock analyzer  114  has a first input connected to the output of the beatnote regulator on line  106  and a second input connected to the output of the counter on line  112 . The lock analyzer  114  analyzes the reset and overflow signals to supply a lock signal at a first output on line  116  when the oscillator and data signal frequencies are within a sufficient tolerance. 
     In normal operation, the lock analyzer  114  generates a lock signal in response to receiving a single overflow signal. The lock analyzer  114  ceases to generate the lock signal in response to receiving a predetermined number of reset signals, subsequent to the initial lock signal. 
     The lock analyzer  114  also has a second output to supply an interrupt signal on line  118  in response to generating an initial lock signal. The beatnote regulator  102  has a second input connected to the second output of the lock analyzer on line  118  to accept the interrupt signal. The beatnote regulator  102  interrupts the supply of reset signals on line  106  that are generated in response to the beatnote signal, when the interrupt signal has been received. The lock analyzer  114  ceases to supply the interrupt signal on line  118  in response to receiving an overflow signal on line  112 , subsequent to the generation of the initial lock signal. Thus, the system  100  ignores the reception of beatnotes in the time period between the generation of an initial lock signal and the subsequent lock signal. This feature is useful when the system  100  uses the lock signal to perform functions that may be momentarily unstable, or that temporarily generate beatnote signals. 
     More specifically, the beatnote regulator  102  generates a single reset signal in response to receiving the interrupt signal, or the initiation of the interrupt signal. This reset signal is used to reinitialize the counter  108 . After generating the next overflow, which in turn causes the subsequent lock signal, the beatnote regulator  102  generates another reset signal in response to the cessation of the interrupt signal. The counter  114  is reinitialized for normal operation where beatnote generated reset signals are once more analyzed. That is, the counter  114  is reinitialized in response to the reset signals generated by the interrupt signal. 
     FIG. 2 is a more detailed depiction of the beatnote regulator  102  of FIG.  1 . In some aspects of the invention, the beatnote signal on line  104  includes a first beatnote signal on line  104   a  responsive to the oscillator signal frequency being higher than the data signal rate. A second beatnote signal on line  104   b  is responsive to the oscillator signal frequency being lower than the data signal rate. A first AND gate  200  has a first input on line  104   a  to receive the first beatnote signal, and a second input on line  104   b  to receive the second beatnote signal. The first AND gate  200  has an output on line  202  that provides the ANDed function of the two input signals. Typically, only one line will have beatnotes to communicate at any particular time, while the other line remains high. The ANDed beatnotes are passed on the line  202 . 
     A rising edge one-shot  204  has an input on line  202  connected to the first AND gate  200  output. The rising edge one-shot  204  creates a pulse supplied at an output on line  206 , in response to each received beatnote. A second AND gate  208  has a first input connected to the second output of the lock analyzer to accept and invert the interrupt signal, a second input connected to the output of the rising edge one-shot  204 , and an output on line  210  to supply the reset signal. In some aspects of the invention (not shown) a degliching circuit may be used between the first AND gate  200  and the rising edge one-shot  204 . 
     An either edge one-shot  212  has an input connected to the second output of the lock analyzer to accept the interrupt signal on line  118 . The either edge one-shot  212  has an output on line  214  to supply a signal in response to the initiation of the interrupt signal and the cessation of the interrupt signal. An OR gate  216  has a first input connected to the output of the either edge one-shot  212  on line  214 , a second input connected to the output of the second AND gate on line  210 , and an output connected to the second input of the counter on line  106 . 
     Although the beatnote regulator  102  has been depicted as a specific combination of logic elements, the present invention is not limited to depicted combination of elements or signal polarities. An equivalent circuit could be easily designed to generate reset pulses in response to equivalent stimuli. 
     FIG. 3 is a more detailed depiction of the lock analyzer  114  of FIG.  1 . The lock analyzer further comprises a first flip-flop  300  having a clock input connected to the counter output on line  112 . A reset input of the first flip-flop  300  is connected to the beatnote regulator output on line  106 . The first flip-flop  300  has an output on line  302  to supply a saved, or gated overflow signal. Note that the data input is tied to a logic high signal and the output is derived from the “Q” output of the first flip-flop in this particular configuration of the invention. 
     A divider  304  has a clock input connected to the output of the beatnote regulator on line  106  and a reset input connected to the output of the first flip-flop on line  306 . The divider  304  has an output on line  308  to supply a divided reset signal. In some aspects of the invention, the divider  304  is a divide-by-four, and the reset signal on line  106  is divided by four. 
     A second flip-flop  310  has a clock input connected to the divider output on line  308 , a reset input connected to the output of the first flip-flop on line  306 , and an output to supply the lock signal on line  116 . The data input of the second flip-flop  310  is tied to a logic high. 
     The lock analyzer  114  includes further elements to enable the interrupt function. A third flip-flop  312  has a data input connected to the output of the second flip-flop on line  116 , a clock input connected to the output of the first flip-flop on line  302 , and a reset input. The third flip-flop  312  has an output on line  314  connected to the reset input, to supply an interrupt reset signal. 
     A fourth flip-flop  316  has a clock input connected to the output of the second flip-flop on line  116 , a reset input connected to the output of the third flip-flop on line  314 , and an output connected to the second input of the beatnote regulator on line  118  to supply the interrupt signal. Note that the data input is tied to a logic high. 
     In some aspects of the invention, the second flip-flop  310  has a first propagation delay for supplying an output responsive to resetting the flip-flop. Then, the lock analyzer  114  further comprises a delay element  318 , with a second propagation delay, and an input connected to the output of the first flip-flop on line  302 . The delay  318  has an output connected to the reset input of the divider  304  and the reset input of the second flip-flop  310  on line  306 . Further, the third flip-flop  312  has a data input hold-time that is less than the combination of the first and second propagation delays. 
     Alternately, the delay element  318  can be eliminated if the propagation of the first flip-flop output signal is delayed sufficiently through second flip-flop  310 . That is, if the third flip-flop hold-time is less than the propagation delay through the second flip-flop. However achieved, the propagation delays are important to assure that the third flip-flop  312  is clocked with a “0”, to prevent the generation of an interrupt reset signal on line  314 . 
     Likewise, the first flip-flop  300  has a third propagation delay for supplying an output responsive to resetting the flip-flop in response to reset signals on line  106 . Then, the divider  304  has a clock pulse processing delay that is less than the combination of the second and third propagation delays. Alternately, the same effect is achieved if the circuit is designed so that the first flip-flop  300  has propagation delay that exceeds the divider clock processing delay. This timing concern insures that the reset signal on line  106  is ignored by the divider  304  (if line  302  is high), before the first flip-flop  300  is reset. 
     Returning to FIG. 1, in some aspects of the invention, the counter  108  has a third input on line  350  to accept commands selecting the first count. Then, the lock analyzer  114  supplies a lock signal with a relaxed tolerance of frequency differences between the oscillator and data signals in response to decreasing the value of the first count. Alternately stated, if the first count is decreased, then it is more likely that an overflow signal will be generated, in turn generating a lock signal, before a reset signal is received. Since it is easier to generate lock signals with a smaller first count, the system has a greater tolerance of beatnotes and, therefore, of frequency differences between the oscillator frequency and data signal rate. Likewise, when the first count is increased, the frequency tolerance is tightened. 
     FIG. 4 is a schematic block diagram illustrating an exemplary use of the system  100  of FIG. 1. A first phase detector  400  has a first input on line  402  to accept the oscillator signal, a second input on line  404  to accept the data signal, a first output to supply the first beatnote signal on line  104   a , and a second output to supply the second beatnote signal on line  104   b . A second phase detector  406  also has inputs connected to receive the oscillator signal and data signal, and has differential outputs on lines  408  and  410 . A Bang-Bang frequency phase detector provides a beatnote signal that is responsive to the frequency of the inputs, and it can be used as the first phase detector  400  to lock a loop or control the frequency of an oscillator. The data signal does not have a frequency per se, however, the information is clocked at a rate which can be thought of as a frequency for the purpose of the present analysis. 
     A switch  412  has a control input connected to the first output of the lock analyzer on line  116  to receive the lock signal. The switch  412  has data inputs connected to the first phase detector  400  on lines  104   a  and  104   b , and to the second phase detector  406  on lines  408  and  410 . The switch  412  selects the second phase detector  406  for use in response to the lock signal on line  116 . The switch  412  selects the first phase detector  400  for use in response to the cessation of the lock signal. 
     In some aspects, the second phase detector  406  is a Hogge phase detector. Then, the circuit of FIG. 4 uses the Bang-Bang  400  and Hogge  406  phase detectors to recover a clock signal from an input data signal. This recovery is accomplished without a reference frequency, and can be designed to meet SONET tolerance standards. The Bang-Bang frequency detector  400  is used in acquisition. When the oscillator  414  frequency is close enough (in frequency) to the data rate, control of the loop is passed from the Bang-Bang frequency detector  400  to the Hogge detector  406  for improved frequency/phase tracking. 
     Additional details of this use of the system  100  for selecting a phase detector can be found in copending patent application Ser. No. 09/667,264, entitled Dual-Loop System and Method for Frequency Acquisition and Tracking, invented by Bruce Coy, filed on Sep. 22, 2000, and assigned to the same assignee as the instant invention. However, the present invention is not limited to merely this specific implementation. 
     A more functional explanation of system  100  follows that requires the simultaneous reference to FIGS. 1 through 4. If the frequency difference between the oscillator signal and the date rate is large, resets occur before the counter  108  can overflow. Likewise, if the frequency difference is within the tolerance of “lock”, the counter  108  overflows before a reset signal is generated. If the counter  108  overflows, an overflow state is triggered and lock is indicated. Once lock is indicated, the lock signal on line  116  cannot change for a time period equal to one entire counter cycle (the first count). After this wait, “lock” can be lost only with four consecutive non-overflow resets (assuming the divider is divide-by-four). This event occurs when the oscillator frequency and the data rate difference are consistently outside of the “lock” tolerance. 
     The lock analysis circuit  114  can start in any internal state and will work itself out within four rising beatnote edges. Assuming the difference in frequency between the oscillator signal and the data rate is more than the “lock” tolerance, the lock signal on line  116 , the gated overflow signal on line  302 , and the interrupt signal on line  118  are low. 
     The first AND gate  200  monitors rising edges of the beatnote signals on lines  104   a  and  104   b . Since the interrupt signal is low, whenever a rising edge occurs a reset signal (high) is generated on line  106 . Assuming that the reset signal is generated before the counter overflows, the gated overflow signal on line  302  is reset before clocking in a “1”, and lock signal on line  116  does not go high. The reset signal also reinitializes the counter  108  and increments the count at divider  304 . When the divider  304  reaches “4”, the second flip-flop  310  clocks in a “1”. 
     As the frequency of the reset signal on line  106  decreases, such that the counter  108  can generate an overflow signal, the lock signal on line  116  goes high. When the gated overflow signal on line  302  pulses high, long enough to reset the second flip-flop  310 , the lock signal on line  116  goes high. At the same time, the divider  304  is reset. 
     Once the lock signal goes high, the interrupt signal on line  118  also goes high. This flag turns “off” the second AND gate  208 , but the action of the either edge one-shot  212 , which generates a pulse in response to either a low or high signal, causes a reset signal, and the counter  108  is reset. The beatnote regulator  102  ignores beatnotes during the time the interrupt signal is high. In the context of FIG. 4, this transition could occur as the switch  412  changes from the first phase detector  400  to the second  406 . The counter  108  is reset so that beatnotes are ignored for the entire 2048 count (assuming the first count equals 2048). When the counter  108  overflows, with the lock signal already high, the third flip-flop  312  is clocked, the fourth flip-flop  316  is reset, and the interrupt signal goes low. The falling edge on the interrupt signal reactivates the second AND gate  208 , and the either edge one-shot  212  causes the counter  108  to reset. Thus, a full count (2048) will occur before the MSB goes high. The divider is also reset, to ensure that four consecutive non-overflow counts are required to lose lock. 
     In some aspects of the invention, the selectable phase detector circuit of FIG. 4 has a 488 parts per million (PPM) tolerance specification. Since any beatnote period over 2048 count indicates 488 PPM frequency difference, or less, between the data rate and the oscillator, it is not desirable to increment the divider  304  when a beatnote reset occurs, after the counter has overflowed. Therefore, it is important that (delayed) gated overflow signal on line  306  is held high and the divider  304  is held in reset, once the counter  108  has reached 2048. 
     Since there is no limit to the period of beatnotes on lines  104   a  and  104   b , an overflow indicator must be used. Also, since a beatnote occurring after a counter overflow should not result in a loss of lock, the divider  304  must be held in reset despite the occurrence of the reset signal on line  106 . 
     An “illegal” initial condition logic circuit can be used to remove the system  100  from the state in which the interrupt signal on line  118  is high and the lock signal on line  116  is not high. In this situation the fourth flip-flop  316  will never be reset. When the counter  108  will overflows, the lock signal remains high, and stays high forever because the interrupt signal is high. In some aspects of the invention (not shown), a simple AND gate has one input connected to accept the interrupt signal on line  118 , a second input to accept an inverted lock signal, and an output to feed an OR gate. The other input of the OR gate is connected to line  314 . The OR output is connected to reset inputs (line  314 ) of the third and fourth flip-flops  312 / 316 . If the system  100  starts up in the interrupt and not locked state, the circuit will go into the not interrupt and not locked state. 
     The following is a case where four consecutive beatnotes, with a period less than 2048 oscillator cycles, cause the system  100  to lose lock. The first beatnote period is 2052 cycles long and all subsequent beatnote periods are 2045 cycles long. 
     
       
         
               
               
             
           
               
                   
               
               
                 VCO CLOCKS 
               
               
                   
               
             
             
               
                   0 
                 reset occurs and counter is set to 0 
               
               
                 2048 
                 counter overflows and rolls back to 0 
               
               
                   4 
                 reset, counter is set to 0 (divider not incremented) 
               
               
                 2045 
                 reset occurs and counter is set to 0 (divider = 1) 
               
               
                 2045 
                 reset occurs and counter is set to 0 (divider = 2) 
               
               
                 2045 
                 reset occurs and counter is set to 0 (divider = 3) 
               
               
                 2045 
                 reset occurs and counter is set to 0 (divider = 4) 
               
               
                   
               
             
          
         
       
     
     The system is out of lock after 4 beatnote periods that are less than 2048 oscillator cycles long. 
     FIG. 5 is a flowchart illustrating the present invention method for determining-frequency tolerance. Although the method is depicted as a sequence of numbered steps for clarity, no order should be inferred from the numbering unless explicitly stated. The method begins at Step  500 . Step  502  measures the frequency of a first signal. Step  504  accepts a measurement of the difference in frequency between the first signal and a second signal. Step  506  reinitializes the measurement of the first signal frequency in response to the frequency difference between the first and second signals. Step  508  determines a sufficient tolerance between the first and second signal frequencies in response to completing the measurement of the first signal frequency. 
     Measuring the frequency of the first signal in Step  502  typically includes counting cycles of the first signal. Then, determining a sufficient tolerance between the first and second signal frequencies in response to completing the measurement of the first signal frequency in Step  508  includes counting a predetermined first number of cycles, or more than the first number of cycles, to obtain a first count. 
     Reinitializing the measurement of the first signal frequency in response to the frequency difference between the first and second signals in Step  506  includes reinitializing the count of the first signal cycles. 
     In some aspects of the invention, the second signal is a data signal with a data rate. Then, accepting a measurement of the difference in frequency between the first signal and a second signal in Step  504  includes generating a reset signal having a frequency that is the absolute difference in frequency between the first signal frequency and second signal data rate. Reinitializing the count of the first signal cycles in Step  506  includes restarting the count at zero in response to the reset signal. 
     Following the determination of a sufficient tolerance between the first and second signal frequencies in Step  508 , Step  510  interrupts the generation of the reset signal. Following the interruption of the generation of the reset signal in Step  510 , Step  512  generates a single reset signal. Step  514  reinitializes the count of the first signal cycles in response to the reset signal. Step  516  counts a first number of first signal cycles. Step  518  ceases the interruption of the reset signal in response counting the first number of cycles. Following the cessation of the interruption of the reset signal in Step  518 , Step  520  generates a single reset signal. Step  522  reinitializes the count of the first signal cycles in response to the reset signal. 
     The method includes the further steps. Step  524  counts at least a predetermined second number of reset signals without an intervening first count. Step  526  determines an insufficient tolerance between the first and second signal frequencies in response to generating reset signals. More specifically, determining an insufficient tolerance between the first and second signal frequencies in response to generating reset signals in Step  526  includes counting the second number of (consecutive) reset signals. Reset signals are considered to be consecutively generated if they occur without an intervening first signal cycle first number count (Step  508 ). 
     In some aspects of the invention, counting at least a second number of (consecutive) reset signals in Step  526  includes disregarding an initial reset signal, subsequent to counting a first number of first signal cycles (the first count). 
     In some aspects of the invention, an oscillator, data signal, and a first phase detector are supplied. Then, measuring the frequency of a first signal in Step  502  includes measuring the frequency of the oscillator signal. Accepting the measurement of the difference in frequency between the first signal and a second signal in Step  504  includes the first phase detector measuring the frequency difference between the oscillator signal frequency and the data signal rate. 
     In other aspects of the invention, a system, using a selectable first and second phase detector, is supplied, as shown in FIG.  4 . Then, in response to determining a sufficient frequency tolerance in Step  508 , Step  509  selects the second phase detector for use in the system. In response to determining an insufficient frequency tolerance in Step  524 , Step  526  selects the first phase detector for use in the system. 
     In some aspects of the invention a further step, Step  501  selects the first number of cycles of first signals to be counted. Then, determining a sufficient tolerance between the first and second signal frequencies in Step  508  includes tightening the tolerance in response to selecting a larger first number of cycles. 
     A system and method have been provided for determining a frequency tolerance between input frequencies without the use of a reference frequency. The invention compares externally generated beatnotes to an overflow count generated by the clock. Although a specific example is given of using the invention to select between phase detectors, and the generation of a oscillator frequency, the invention is applicable to other types of frequency or loop analysis. Other variations and embodiments of the invention will occur to those skilled in the art.

Technology Category: 4