Patent Document

This application claims priority to International Application No. PCT/DE01/01621, which was published in the German language on Nov. 1, 2001. 

   TECHNICAL FIELD OF THE INVENTION 
   This invention relates to a circuit arrangement to produce wander or wander sequences. 
   BACKGROUND OF THE INVENTION 
   Wander and wander sequences with a frequency below 10 Hz are used in the testing and measurement technologies to investigate the behavior of signal transmission circuits toward signals with very long periods. Thus, the use of wander or wander sequences in connection with synchronous digital signal transmission is required, as for example is indicated in the ITU-T Recommendation G.823 (03/93). 
   Up to this point, wander or wander sequences of the type cited above could only be produced through relatively high degrees of device engineering. In the process, function-modulating and frequency-modulating signal generators were used, which, however, led to the required wander amplitudes being issued at low clock frequencies and in all cases with a very high degree of circuitry. 
   SUMMARY OF THE INVENTION 
   This invention relates to a circuit arrangement to produce wander or wander sequences that have frequencies below 10 Hz, in particular below 1 Hz, with a frequency divider circuit that receives impulse signals of relatively high frequency as incoming inputs and that issues impulse signals of divided frequency at its output side from which the respective wander or the respective wander sequence is built. 
   The invention discloses a circuit arrangement of the type cited above with relatively little circuitry to produce wander or wander sequences whose frequencies lie below 10 Hz and preferably below 1 Hz. 
   According to one embodiment of the invention, there is a circuit arrangement where the frequency division circuit has two individual dividers, each of which encompasses a counting arrangement that receives as incoming inputs the impulse signals mentioned having the relatively high frequency, the count cycle of one counting arrangement is changed with respect to the count cycle of the other counting arrangement within the period of the respective wander or wander sequence to be produced according to a desired shape of this wander or wander sequence, and a phase comparator circuit is connected at the outputs of the two counting arrangements, from the output of which the respective wander or the respective wander sequence can be taken. 
   One advantage of the invention is an especially low amount of circuitry in producing wander or wander sequences below 10 Hz and preferably below 1 Hz. Using two counting arrangements, and by changing the count cycle of one counting arrangement with respect to the count cycle of the other counting arrangement in the manner described, the prerequisites are met for obtaining the respective desired wander or wander sequence by means of a phase comparator circuit connected after the outputs of the two counting arrangements. 
   To this end, a low pass filter is connected after the phase comparator circuit mentioned. This provides the advantage in that the respective wander or respective wander sequence obtains a desired smooth shape. 
   It is preferable for each counting arrangement to be connected at the output of its own oscillator circuit. In this way, other changes can be made in the respective wander or wander sequence if necessary by correspondingly controlling at least one of the two oscillator circuits. 
   A particular advantage is if each oscillator circuit belongs to a separate PLL circuit. In this way, the respective wander or wander sequence can be produced with very good stability, i.e., with very low jitter. Due to the resultant influence on the counting arrangement in the output circuit of one of the PLL circuits, the required output amplitude of the respective wander or wander sequence to be produced can be produced with a high degree of stability by changing the counter value of the affected counting arrangement within a defined count cycle. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
     The invention is explained in more detail below with the help of the drawings as an example. 
       FIG. 1  shows a block diagram of a first exemplary embodiment of the circuit arrangement according to the invention. 
       FIG. 2  shows a block diagram of a second exemplary embodiment of the circuit arrangement according to the invention. 
       FIG. 3  shows a diagram of the temporal shape of impulses or signals that occur at various points in the circuit for the circuit arrangement illustrated in  FIGS. 1 and 2 . 
       FIG. 4  shows a diagram of the temporal shape of the wander or of a wander sequence that occurs at other points in the circuit for the circuit arrangement illustrated in FIGS.  1  and  2 . 
   

   DETAILED DESCRIPTION OF THE INVENTION 
   The circuit arrangement shown in  FIG. 1  illustrates a first exemplary embodiment, according to the invention, and encompasses a frequency division circuit that has two individual dividers CNTa, CNTb, each of which encompasses a counting arrangement, and to which input impulses of relatively high frequency, for example impulses with a frequency of 8 kHz, are fed at a common input connection IN that can be derived from impulses with a frequency of, for example, 16,384 MHz. The generator circuit that produces these impulses operate at very high precision (10 −12 ) so as to be able to make available the desired wander or wander sequences. Each of the two individual dividers mentioned, CNTa, CNTb —which basically both have the same division ratio, i.e., are built in the same way —includes a counting arrangement that is made up of two partial, or individual counters C 11 , C 12  and C 21 , C 22  connected in series, of which the partial counters C 11 , C 21  perform a first coarse division of the input impulses and of which the partial counters C 12 , C 22  execute the final conversion. In principle, each counting arrangement can also be made up of only one counter. 
   Control outputs of a control circuit CTR 1  are connected to adjustment inputs of the partial counter C 22  belonging to the individual divider CNTb and, if necessary, also to adjustment inputs of the partial counter connected to it, C 21 . The affected control circuit CTR 1  is connected to a control input at an input connection Cin and to a signal input at the output of the partial counter C 22 . By means of this control circuit CTR 1 , the count cycle of at least partial counter C 22  can be changed with respect to the count cycle of its corresponding partial counter C 12  belonging to the other individual divider CNTa within the determined period of the respective wander or wander sequence to be produced according to a desired shape of this wander or wander sequence, as is further explained below in connection with  FIGS. 3 and 4 . 
   At the outputs  01  and  02  of the two individual dividers CNTa and CNTb is a phase comparator circuit COMg, the input side of which is connected according to FIG.  1 . At the output  03  of this phase comparator circuit COMg, which is indicated as a circuit containing an AND gate, a low pass filter TPFg is connected whose output is connected to an output  04  of the circuit arrangement. 
   The respective desired wander or wander sequences can be taken at the two outputs  03  and  04  just mentioned. More detail will be provided on this in connection with FIG.  4 . 
     FIG. 2  shows a further development of the circuit arrangement shown in  FIG. 1  as a second exemplary embodiment of the invention. According to  FIG. 2 , the counting arrangements includes two partial counters each, or CNT 1   a  and CNT 1   b  and CNT 2   a  and CNT 2   b  —for which the same specifications apply that had been made with respect to the partial counters CNTa, CNTb according to  FIG. 1  —are each connected to the output of a separate oscillator circuit OSC 1  and OSC 2 ; the inputs of the two oscillator circuits OSC 1  and OSC 2  are each connected to the output of a low pass filter TPF 1  and TPF 2 . 
   Each of the two oscillator circuits OSC 1  and OSC 2  belongs to a separate PLL circuit, PLL 1  and PLL 2 , within which they are each connected to the output of an associated phase comparator circuit COM 1  and COM 2  with its respective low pass filter TPF 1  and TPF 2 . These phase comparator circuits COM 1  and COM 2  are connected in common through one of their inputs to an input terminal identified by IN, to which, in this case, input signals are fed having relatively high frequency, for example impulses with a frequency of 8 kHz, which can be derived from impulses with a frequency of 16,384 MHz, for example. The generator circuit producing these impulses must also operate here with very high precision (10 −12 ) in order to be able to make available the desired wander or wander sequences. The 8 kHz input signal mentioned provides reference impulses or signals in the circuit arrangement according to FIG.  2 . The other inputs of both phase comparator circuits COM 1  and COM 2 , each of which is likewise represented as a circuit containing an AND gate, are connected to an output of the counting arrangement that is connected after the respective oscillator circuit OSC 1  and OSC 2 . In this case, the outputs O 1  and O 2  of the partial counters CNT 1   b  and CNT 2   b  are connected to the applicable inputs of the phase comparator circuit COM 1  and COM 2 . However, it is, in principle, also possible to connect the outputs of the other partial counters CNT 1   a  and CNT 2   a  to the applicable inputs of said phase comparator circuits COM 1  and COM 2 . 
   As in the circuit arrangement shown in  FIG. 1 , control inputs of at least the partial counter CNT 2   b  and, if necessary, also of partial counter CNT 2   a , are connected to control outputs of a control circuit CTR 2  in the circuit arrangement shown in FIG.  2 . These control outputs can correspond to the control circuit CTR 1  shown in FIG.  1 . Accordingly, the applicable control circuit CTR 2  is connected to a control input at an input terminal Cin and to a signal input at output O 2  of the partial counter CNT 2   b.    
   A phase comparator circuit COM 3  is connected after the two counters shown in  FIG. 2  to their outputs and includes on one hand the partial counters CNT 1   a  and CNT 1   b , and on the other the partial counters CNT 2   a , CNT 2   b . At the output  03  of the phase comparator circuit, a low pass filter TPF 3  is connected after it, whose output is connected to an output O 4 . The phase comparator circuit COM 3  and the low pass filter TPF 3  correspond to the phase comparator circuit COMg and the low pass filter TPFg in the circuit arrangement shown in FIG.  1 . 
     FIGS. 3 and 4  explain the principle of generating wander or wander sequences as it is applied to this invention. In this regard, mention should be made that in principle both circuit arrangements according to  FIGS. 1 and 2  operate in the same manner with regard to the generation of wander or wander sequences with very small frequencies below 10 Hz, and preferably below 1 Hz. 
   The diagram shown in  FIG. 3  shows impulses or signals occurring at various circuit points of the circuit arrangements illustrated in FIG.  1  and  FIG. 2  along the time axis t. In the row identified by IN are the input impulses occurring at the input terminals IN in the circuit arrangements according to  FIGS. 1 and 2  that may occur with a relatively high frequency of 8 kHz and which can be derived from a signal with a frequency of 16,384 MHz, for example. In the case of the circuit arrangement according to  FIG. 1 , these input impulses experience a frequency division in both partial counters CNTa and CNTb, so that final output signals occur at the outputs O 1  and O 2  indicated in  FIG. 1  that are illustrated in the correspondingly named rows in  FIG. 3 , for example with a frequency of 8 kHz each. The same applies for the partial counters CNT 1   a , CNT 1   b  and CNT 2   a , CNT 2   b  in the circuit arrangement according to FIG.  2 . 
   According to  FIG. 3 , the leading edges of the impulses indicated in row O 2  are shifted with respect to the leading edges of the corresponding impulses in row O 1  by one cycle each of the impulses shown in the upper row IN in  FIG. 3  relative to the preceding time of observation shown, respectively. This shift occurs according to  FIG. 3  relative to the impulses shown in row O 1  in one direction (to the right in FIG.  3 ). In the process, the change in this direction can occur over a time frame corresponding to n/2 of the period of the wander or wander sequence to be issued, whereupon a change in the applicable leading edges of the impulses shown in row O 2  can then occur with respect to the leading edges of the impulses shown in row O 1  in the other direction (i.e., according to  FIG. 3  to the left) during a duration of n within the period of the wander or wander sequence to be issued. Then, a change can again finally take place in the leading edges of the impulses shown in row O 2  relative to the leading edges of the corresponding impulses shown in row O 1  in  FIG. 3  in the manner explained above (i.e., to the right in  FIG. 3 ) during a duration of n/2 within the period of the wander or wander sequence to be issued. 
   The shift explained above in the leading edges of the impulses of the output signal shown in row O 2  in  FIG. 3  with respect to the leading edges of the impulses of the output signal shown in row O 1  in  FIG. 3  occurs by correspondingly adjusting the partial counter C 22  shown in  FIG. 1  or of the partial counter CNT 2   a  shown in  FIG. 2  by means of the control circuit CTR 1  or CTR 2  connected to its control inputs. In the process, this control circuit CTR 1  or CTR 2  changes, firstly, the count cycle of the applicable partial counter C 22  or CNT 2   a  with respect to the count cycle of the other corresponding partial counter C 12  or CNT 1   a  within the period of the wander or of the wander sequence to be produced, and secondly, this change occurs according to the desired shape of this wander or wander sequence. In order to further clarify this statement, reference is made to the diagram shown in FIG.  4 . 
   The diagram according to  FIG. 4  shows in an amplitude-time axis diagram the temporal shape of the output signals occurring at the output O 3  and at output O 4  in the circuit arrangement according to FIG.  1  and  FIG. 2  (wander or wander sequence) along the time axis t. In the process, the output signal occurring at the output, i.e., output terminal O 3  shows a triangular shaped curve having a positive value within the time frame from 0 to n and a negative shape within the time frame from n to 2n directly adjacent to it. The time frame from 0 to 2n represents one period of the wander or wander sequence to be produced. 
   The triangular shaped output signal with the stepped stages is produced based on the relationships that had been explained before in connection with  FIG. 3 , with respect to the impulses or output signals shown in rows O 1  and O 2 . In the process, the respective step height (amplitude) of this output signal shown in  FIG. 4  by O 3  depends on the phase difference between the output signals occurring in rows O 1  and O 2  according to  FIG. 3 , and accordingly at the corresponding circuit points according to FIG.  1  and  FIG. 2 , the output signals being processed by the phase comparator circuit COMg or COM 3 . However, the respective step width (in the direction of the time axis) depends on the duration during which the amplitude mentioned before is to be issued within the period ( 0 -2n) of the wander or wander sequence to be produced. This means that a corresponding adjustment of the partial counter C 22  occurs by means of the control circuit CTR 1  or CTR 2  for this duration. 
   In order to be able to execute the adjustment of the partial counter C 22  mentioned, a corresponding control signal can be fed to the control circuit CTR 1  at its control input or input terminal Cin, which first establishes the respective duration during which the respective adjustment of the partial counter C 22  or CNT 2   a  is to remain (step width), and which secondly establishes the number of changes of the partial counter C 22  or CNT 2   a  for the change of its counter position relative to the counter position of the other corresponding partial counter C 12  or CNT 1   a  (amplitude), as had been explained in connection with FIG.  3 . To be able to execute this control action, the control circuits CTR 1  and CTR 2  are each connected to a signal input at the circuit point or output O 2  according to  FIGS. 1 and 2 . 
   The sinusoidal output signal O 4  is then formed from the output signal O 3  shown in  FIG. 4  by means of the low pass filter TPFg or TPF 3  in the circuit arrangement according to  FIG. 1  or according to  FIG. 2 , which is issued by the corresponding output or output terminal O 4  of the circuit arrangement according to  FIGS. 1 and 2 . This means that a smoothing of the triangular output signal O 3  leads to output signal O 4 . A corresponding smoothing of the output signal of the phase comparator circuit COM 2  takes place as well in the circuit arrangement shown in  FIG. 2  by means of the low pass filter TPF 2 . This smoothing results in a stable control voltage being fed to the oscillator circuit OSC  2  according to  FIG. 2 , which leads to the issuance of an oscillator output signal with stable frequency. 
   Based on the count values given above for the impulses occurring at the respective input terminal IN as well as at the outputs O 1  and O 2  in the circuit arrangements according to  FIGS. 1 and 2 , a wander or wander sequence can be obtained from the output O 3  or O 4  of this circuit arrangement, as shown in  FIG. 4  with a frequency of 12 μHz, for example, which corresponds to a period T=23,148 h. In the process, the shape shown in  FIG. 4  of the wander sequence can occur [be produced] in 295 steps for example (time axis t). 
   Finally, mention is made that the phase comparator circuits contained in the circuit arrangements shown in  FIGS. 1 and 2  are preferably phase-sensitive phase comparator circuits, i.e., phase detectors or Type 2 PD systems as they are called in the literature (see for example the book “Einfóhrung in die PLL-Technik,”[Introduction to PLL Technology], H. Geschwinde, Verlag Priedr. Vieweg &amp; Sohn, Braunschweig/Wiesbaden, 1980, beginning at page 118, and the book “Theorie und Anwendung des phase-locked-loops” [Theory and Application of Phase Locked Loops], Roland Best, AT Verlag Aarau/Schweiz, 1993, pages 96-99). 
   Otherwise, the circuit arrangement according to the invention is not just suited for the generation of sinusoidal wander or wander sequences, as had been described above, but that in general also wander or wander sequences with other forms can be generated. As can be seen, the establishment of these forms occurs through correspondingly issuing control signals from the control circuit CTR 1  or CTR 2  in the circuit arrangements according to  FIGS. 1 and 2 , which are separately controlled from them. Referring to the circuit arrangement according to  FIG. 2 , it should also be mentioned that its oscillator circuits OSC 1  and OSC 2  can be separately adjusted if necessary in order to generate an even larger variety of wander or wander sequences than is possible using the control circuit CTR 2 .

Technology Category: 5