Patent Document

RELATED APPLICATIONS 
     U.S. application for patent entitled &#34;Flowmeter System with a Synchronous Clock for Generation of Timing Signals&#34; by R. S. Loveland, filed even date herewith, Ser. No. 224,783; 
     U.S. application for patent entitled &#34;Flowmeter System With Ultrasonic Energy Improvement in Equillibration&#34; by R. S. Loveland, filed even date herewith, Ser. No. 224,783; 
     U.S. application for patent entitled &#34;Flowmeter System With Improved Dynamic Range&#34; by R. S. Loveland, filed even date herewith, Ser. No. 224,725; and 
     U.S. application for patent entitled &#34;Flowmeter System With Digital Phase Shifter and Calibration&#34; by R. S. Loveland, filed even date herewith, Ser. No. 224,723. 
     BACKGROUND OF THE INVENTION 
     This invention relates to acoustical flowmeter systems and is particularly directed to an improvement in the acoustical flowmeters of the type described and claimed in the U.S. Pat. No. 4,003,252 entitled &#34;Acoustical Wave Flowmeter&#34; by E. J. DeWath which issued Jan. 18, 1977 and the flowmeter system of the type described and claimed in the U.S. Pat. No. 4,164,865 entitled &#34;Acoustical Wave Flowmeter&#34; by L. G. Hall and R. S. Loveland which issued Aug. 21, 1979. 
     The invention of DeWath was directed to a flow meter having an unobstructed tubular wall thereby eliminating all impediments to the flow path of the fluid and eliminating all cavities in which debris might collect. The advantages of such a configuration is fully set forth in the DeWath patent. To measure flow of a selected fluid in the DeWath flowmeter, however, required a calibration for that particular fluid and required a recalibration if the flow of a different fluid was to be measured since the flowmeter was not responsive to changes in fluid species or densities. 
     The Hall and Loveland invention improved the DeWath flowmeter by providing a flowmeter that measured flow accurately regardless of changes in fluid composition or temperature and by providing a flowmeter with a means for determining a change in velocity of sound of the fluid being measured. 
     In order to accomplish this, the Hall and Loveland acoustical wave flowmeter system had two spaced apart crystal transducers in the wall of the flowmeter conduit (sometimes called a cavity) to produce ultrasonic acoustic compressions at selected frequencies in the fluid within the cavity. The transducers were alternately switched into a transmit and a receive mode to generate upstream and downstream transmitted and received signals with an automatic means to adjust the transmitted frequencies to compensate for changes in velocity of the acoustic compressions in the fluid caused by changes in fluid composition and temperature. The electronic circuitry involved in the Hall and Loveland flowmeter system include means for measuring and storing signals representing the phase difference between the transmitting transducer signal producing the acoustic compressions and the signal produced by the receiving transducer during each of two successive transmit/receive cycles. Circuit means were provided to determine the difference between the signals representing the two successive phase differences wherein the sign of the difference corresponds to the direction of the fluid flow and the magnitude of the difference corresponds to the rate of fluid flow through the flowmeter. Circuit means were also provided to add the two successive phase difference signals together to obtain a signal proportional to the velocity of sound in the fluid moving through the flowmeter. This latter signal indicated the change in composition of the fluid flowing through the meter. 
     The Hall and Loveland flowmeter system had a phase lock loop in the receiver/transmitter system which included, among other circuit components, a phase detector, voltage controlled oscillator (VCO) and a loop filter. This loop filter was a passive filter of the RC type for filtering the error voltage signal applied to the VCO which would respond by changing the transmitted frequency of the transducer. The problem encountered with this system is that, once calibrated to operate at a certain fluid density, a change in fluid density, for example, would cause the VCO to operate at a different frequency which means that the phase detector has a constant phase error to create the voltage to drive the VCO to a new frequency and thus the range of the phase detector for measuring the magnitude of flow was thus limited. For example, if the offset, or voltage applied to the VCO, were to change one volt, this would mean that the output of the phase detector would be required to work at a greater phase error difference from that for which the system was calibrated. Thus, with less phase error to work with, the flow measurement range is decreased, making the system more sensitive to changes in fluid flow or density which could cause the entire system to go out of range or into an out-of-lock mode. 
     This invention improves the prior system by requiring only a very small phase error to be detected by the phase detector in order to change the error signal applied to the VCO by a large amount thus improving the loop gain of the system. Accordingly, it is a primary object of this invention is to improve the loop gain of a phase lock loop circuit in a flow meter system. 
     SUMMARY OF THE INVENTION 
     The flowmeter system which meets the foregoing object comprises means defining a path for confining the flow of a fluid medium therethrough, first and second transducers disposed along said flow path for generating and receiving acoustic compression waves in the fluid medium between the transducers, circuit of the phase lock loop type having means for automatically adjusting the frequency of the acoustic compression waves to maintain the compression wave length constant in the fluid medium, means for measuring the phase difference of the acoustic compression waves transmitted upstream and downstream relative to that received and for producing a sum and difference signals dependent upon the difference between the transmit and receive two phases and transmitting said signal to said means for automatically adjusting the frequency of the acoustic compression waves, means for generating signals representing the direction and magnitude of the flow of the fluid medium as well as changes in the velocity of sound in the fluid medium, and an active filter including an operational amplifier whose output is connected to the input of the means for adjusting the frequency of the acoustic compression waves is that the gain of the phase lock loop so increased by the gain of the active filter thus reducing the need for large changes in phase difference to be detected by the phase detector before a change is augmented by the means for adjusting the frequency of the acoustic compression waves. 
     Other objects and advantages of this invention will become apparent to those skilled in the art after a study of the drawings and detailed description hereinafter. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is a simplified blank diagram of the flowmeter system of the invention, 
     FIG. 2 is the prior art passive filter, 
     FIG. 3 illustrates the received, as transmitted and phase detected pulses of the phase detector, 
     FIG. 4 illustrates the circuit for the active filter of this invention, and 
     FIG. 5 illustrates the total open loop gain of the system by incorporating this invention. 
    
    
     DETAILED DESCRIPTION 
     FIG. 1 illustrates the flowmeter system of the present invention which includes a transducer assembly 10, shown in longitudinal section, which comprises a substantially cylindrical body having a central cylindrical opening, or bore 12, through which a fluid medium flows in both directions, as indicated by the arrows 14. 
     The transducer assembly is made generally in accordance with the description in the U.S. patent to DeWath, supra, and is provided with spaced apart cylindrical crystal transducers whose inner diameters are substantially coextensive with the cylindrical bore 12 so that the wall is substantially uniform with no obstructions or cavities to provide a place for particulate matter to collect or to provide an impediment for the flow of fluid therethrough. The purpose of the transducers is described in the DeWath patent and in the Hall and Loveland patent, supra. 
     While the Hall and Loveland patent also showed and described, in great detail, control circuitry for operating the crystal transducers to accomplish the desired results, for the purpose of this invention, this circuitry has been simplified into block diagrams and reference can be made to this patent if more detailed information on the operation of the circuit is thought necessary. 
     As can be seen in FIG. 1, the two ultrasonic crystal transducers, represented by crystals 16 and 18, also identified as CR D  and CR U , are alternately each connected to the transmission control circuitry via a switching mechanism 20. When one transducer is connected to the transmission circuitry via switching mechanism 20, the other transducer is in the receive mode the output of which in turn is connected via a second switching mechanism 26 to a phase detector 28, a signal integrator 30 and two sample-and-hold circuits 32 and 34, identified as upstream and downstream. The outputs of these two sample-and-hold circuits are connected to two operational amplifiers, one identified as a summing amplifier 36 and the other identified as a difference amplifier 38. The output of the summing amplifier 36 will indicate the velocity of sound and the output of the difference amplifier will indicate the magnitude and direction of the measured fluid flow. The output of the summing amplifier is connected to a loop filter 40 and to a voltage controlled oscillator 42 (VCO) which is connected back to the phase detector 28 and to a phase shifter and square-wave-to-sine wave converter 44. The phase shifter and converter 44 output is connected back to the first switching mechanism 20. Also like the summing amplifier, the output of the difference amplifier 38 is connected to the VCO 42 but through a multiplier 46 and a velocity of sound conditioning circuit 48. One output of the multiplier is the magnitude and direction of the fluid flow as stated above and the second output represents the relative velocity of sound. Shown connected by dotted lines are the first and second switching mechanisms 20 and 26 and two additional switching mechanisms 50 and 52 all under the control of a combinational logic and clock circuit 54. The circuit 54 alternates transmit and receive functions of the two crystal transducers 16 and 18, alternates the output of the upstream and downstream receivers 22 and 24, operates the integrator 30 between reset, integrate and hold functions and, finally, operates the upstream and downstream sample-and-hold circuits 32 and 34 through a sample, hold, and sample function. 
     As shown in this Figure, the ultrasonic crystals 16 and 18 are alternately switched into either the transmit or receive mode by the combinational logic circuit. Thus, while one crystal is receiving, the other crystal is transmitting. 
     For each transmit/receive cycle, the phase difference between the transmit signal and the received signal is detected by the phase detector 28. The average value is determined for each transmit/receive cycle by the integrator circuit 30 which goes through an integrate, hold and reset mode for each transmit/receive cycle. During each integrator hold period, the respective sample/hold circuit for the upstream phase and the downstream phase is ready to accept the new signal (sample mode) as data is available at the integrator output. The upstream and downstream sample/hold circuits are updated with new data at the end of each respective transmit/receive cycle and stores (holds) the information during the wait period. 
     In the differential amplifier 38, the stored values are then subtracted with the output indicating the direction and magnitude of the fluid flow. In addition, the same stored values are added together in the summing amplifier to determine if a common mode change has occurred in the fluid medium. A common mode change is caused by a change in the velocity of the ultrasound which, in turn, may be due to either temperature or fluid species change. The result is that the sum of the upstream and downstream data, held by the respective sample-and-hold circuits, changes in a manner which causes an error voltage signal at the voltage controlled oscillator (VCO) 42 input to change the transmit frequency in a direction which returns the wave length of the ultra-sound frequency is its original value thereby keeping the wave length constant. 
     The components of the control circuitry thus far described correspond to the control circuitry of the flowmeter system of the Hall and Loveland patent; it being understood that the foregoing is a simplification of the patented control circuitry. For example, the switching mechanism 20 in this disclosure is actually a combination of high speed transistorized switches comprised of transistors Q1 thru Q8 controlled from the clock source by pulses X,Y Q3 and Q3 applied to their respective inputs, switching mechanism 26 are transistors Q9 and Q10 with pulses A and B applied to their respective inputs operation of the logic and clock source but otherwise the block diagrams correspond to the patented circuitry, etc. Other switching mechanisms exist in the circuitry of the patent through the operation of the clock source but otherwise the block diagrams correspond to the patented circuitry. It is understood that the other switching mechanisms were shown here to illustrate the operation of the circuitry in the block diagram only. 
     As hereinabove, stated, this invention improves the patented system by increasing the loop gain (gain is a function of components in the loop, eg, transducers, loop filter, integrator, VCO, etc), and this is accomplished by incorporating a new and improved loop filter into the flowmeter system. However, in order to understand the significant improvement in loop gain the prior art loop filter as used in the patented system will first be described. In connection with this, attention is now directed to FIGS. 2,3, and 4, where FIG. 2 is the prior art passive loop filter, FIG. 3 illustrates the phase detector input (transmitted and received) and output pulses, and FIG. 4 illustrates the improved active loop filter comprising this invention as part of the flowmeter system. 
     As illustrated in FIG. 2, and as described in the Hall and Loveland patent, output pulses from the summing amplifier 36 are applied to the passive loop filter 40 which comprises a one megohm resistor R and a one micro-farad compacitor C connected in a conventional manner with the output therefrom applied directly to the input of the VCO 42. This filter, being passive, simply filters the input signal with no gain so that its output is simply a filtered voltage signal of essentially the same amplitude as the input pulse. 
     To understand the need to improve loop gain, attention is now directed to FIG. 3 showing the timing pulses where line A represents the transmit pulses applied to one transducer generating the acoustic compression waves in the fluid medium and line B represents the received pulses received from either the upstream or downstream receiver and applied to the phase detector 28 under a no flow condition with a fluid for which the instrument has been calibrated. Thus, the received pulses are 90° out of phase with the transmitted pulses under a calibrated ideal condition. Line C represents the output of the phase detector under such a condition. Note the pulses in line C are 1/2 the length of the pulses in lines A and B at twice the frequency of the received pulses. 
     However, in use, when the summing amplifier 36 indicates a change in density of the fluid in the cavity, an error signal is applied to the VCO 42 so as to change the frequency of the transmit pulses applied to the transmitting transducer so that the wavelength of sound through the newly detected changed fluid remains the same. For example, as seen in line D of FIG. 3, considering the transmitted frequency which has changed due to a fluid density change, as a constant, the received pulses have moved in phase relative to the transmitted pulses, as for example 30° on one side and 60° on the other side from its original position of 45° on both sides. This means that when the detected phase offset is as shown in line D, the system can only respond to a further shift of 30° (due to a flow signal) in the direction which is already at 60° before the maximum limit of 90° is reached before the system goes to an out-of-lock mode--an inoperative mode. Translating this into fluids being measured, for example, if the original instrument was calibrated to respond to a change of 6 liters per second in its original calibration, the system would only be capable of measuring 4 liters per second since 1/3 (60°-45°) of phase detector range has been used to change the VCO frequency. Thus, a change of flow of greater than 4 liters per second in one direction would throw the system into an out-of-lock mode. 
     What this means, is that, in the prior art, in order to have a change in phase error signal of one volt, wave form D would change its duty cycle. The duty cycle of wave form C is 50 percent and the signals entering the phase detector are exactly 90° (when calibrated) out of phase, but if the fluid density is changed, then the duty cycle of the wave form must change. In changing the duty cycle of this wave form, however, the range in one direction is not the same as the range in the other. Thus, a sudden change of fluid in the wrong direction would cause the system to go into an inoperative mode. 
     Explaining the operation of the flowmeter system in another way, and to thus inferentially explain the importance of this invention, attention is directed back to FIG. 1 where the upstream and downstream sample-and-hold circuits 32 and 34 have their outputs, respectively, identified as φ U  and φ D , applied to the sum and difference amplifiers 36 and 38. 
     Turning now to FIG. 4, there is shown an active filter 40 which comprises a resistor R1 connected to the inverting input of an operational amplifier 70 and also connected through a second resistor R2 to a capacitor C1 which, in turn, is connected to the output of the operational amplifier. The noninverting input to the amplifier is grounded. The active filter is essentially an integrator, where C1 is the integrating component, R1 defines the unity gain crossover frequency and R2 is used for loop stability. Thus, the voltage applied to this active filter 40 is multiplied several hundred thousand times according to, or equal to, the gain of the operational amplifier. It becomes apparent, then, that a minute change in density will cause a large error signal to be applied to the VCO to change the transmit frequency. Thus, the 50% duty cycle wave form remains virtually unchanged and the dynamic range of the system is substantially uneffected. 
     How this increases the loop gain by a tremendous amount is explained further in connection with FIG. 5 which represents the open loop transfer function of the phase lock loop system--gain versus frequency. As can be seen, as frequency is increased, the 3 db roll off point is reached at about 0.16 hertz and it continues to roll off until it reaches about 16 hertz. With the open loop gain of this system at about 100, the error voltage required to change the VCO frequency, is relatively high. This is true regardless of whether the phase detector is the one of the prior art or the new phase detector which is the subject matter of the currently filed U.S. patent application Ser. No. 224,725, supra. 
     However, by replacing the passive filter of the prior art with the active loop filter, this loop gain increases by at least a hundred thousand, that is, the gain of the amplifier (shown by the dash line below 0.16 hertz point) times the gain of the loop provides a total open loop gain as a product of these two or 100,000×100. Thus, again the system maintains the 50 percent duty cycle wave form and the dynamic range of the system remains substantially unaffected by the change in flow or fluid density. 
     It should be apparent from the foregoing that this invention may be incorporated into the circuitry of the Hall and Loveland patent, supra, to improve its performance, or may be incorporated in circuitry improved by the incorporation of any one or all of the inventions identified under RELATED APPLICATIONS. supra into a circuit to improve the performance of such circuitry. If the invention of the application Ser. No. 224,783 is not used, of course, line 56, shown herein, would be omitted.

Technology Category: g