Patent Document

PRIORITY 
     This application is a continuation of U.S. application Ser. No. 12/852,864, filed Aug. 9, 2010, the disclosure of which is incorporated herein by reference. 
    
    
     TECHNICAL FIELD OF THE INVENTION 
     The present invention relates in general to spatial and temporal overlapping of pulses multiple pulsed gas-discharge lasers. The invention relates in particular to spatial and temporal overlapping of pulses from two or more excimer lasers or molecular-fluorine lasers. 
     DISCUSSION OF BACKGROUND ART 
     Excimer lasers are pulsed gas lasers that deliver radiation in the ultraviolet (UV) region of the electromagnetic spectrum. There are applications of such lasers, for example, laser annealing, that would benefit from a pulse-energy greater than available from the highest energy excimer laser presently available. A greater pulse-energy can be supplied by combining the output of two or more excimer lasers. The output of the lasers must be overlapped spatial and temporally. The spatial overlap can be achieved precisely using an arrangement of optical elements, and optical overlap methods are well known in the art. 
     The temporal overlap is less precise and depends on the precision which operating characteristics of pulsed power supplies, among other factors, can be reproduced from pulse to pulse. Variation of such characteristics leads to temporal variation of the precision of pulse-overlap. This temporal variation is usually referred to by practitioners of the art as jitter. Depending on the pulse duration and on application requirements, there is usually a jitter value that can not be exceeded without compromising the application. 
     By way of example, in a laser annealing application, it may be required to combine the pulsed output of two excimer lasers having a pulse repetition rate of about 600 Hertz (Hz) and a pulse-duration of about 30 nanosecond (ns) full-width at half-maximum (FWHM), with pulses having a complex temporal pulse-shape. Maintenance of a complex temporal pulse-shape is possible only if the pulses are overlapped precisely in time. The tolerance of an application toward variations in the temporal pulse-shape in the overlapped beam cannot be stated in general, and depends on the sensitivity of the application with respect to the pulse shape. For applications in the laser annealing area, this tolerance level corresponds to jitter of a few nanoseconds, for example less than about 6 ns for the 30 ns pulse-duration. 
     In order to understand the factors affecting jitter, it is useful to consider characteristics of pulsing circuit arrangements for an excimer laser. A description of one such circuit arrangement is set forth below with reference to  FIG. 1 , which is a circuit diagram depicting one typical arrangement  10  of circuitry for delivering high voltage pulses to discharge electrodes of an excimer laser. 
     Here, high-voltage power (HV-IN) power from a high-voltage power supply (HVPS) is supplied to a terminal  12 . The power is used to fully charge a storage capacitor C 0  to a predetermined voltage, typically between about 1500 and 2300 Volts (V). The capacitor is charged via a magnetic isolator  14 . Magnetic isolator  14  includes a diode D 2  and a transformer L 6 , one side which is connected to a switch  16  including an isolated-gate bi-polar transistor (IGBT) and rectifier bridge, and other components (not shown). An inhibit signal can open or close switch  16  as required. 
     Magnetic isolator  16  switches the impedance value between the HVPS and storage capacitor by a factor of about 50 from a low value to a high value (and vice versa) depending on whether switch  16  is respectively closed or open. The low impedance value is needed to charge capacitor C 0  with high precision. The higher impedance value is necessary to protect the power supply from energy reflected back from the laser discharge, which could otherwise cause very high and potentially destructive peak currents through the power supply. Only sufficient description of magnetic isolator  14  is provided here to understand the operation of circuitry  10 . A detailed description of the magnetic isolation principle is provided in U.S. Pat. No. 6,020,723, assigned to the assignee of the present invention, and the complete disclosure of which is hereby incorporated herein by reference. 
     When charging of capacitor C 0  is complete, magnetic isolator  14  is switched to the high impedance condition. Discharging of capacitor C 0  is controlled by an IGBT and diode (“free-wheeling diode”—FWD) module IGBT-1. On receipt of a pulse-trigger voltage at the gate of IGBT-1 the IGBT is closed and capacitor C 0  is discharged through a magnetic-assist L 5 , a pulse-transformer L 4 , and a diode D 1 . The resultant pulse from transformer L 4  is sent to a pulse-compressor  18 . The pulse is compressed in three stages formed by saturable inductor or magnetic switch L 1  and capacitor C 1 , saturable inductor L 2  and capacitor C 2 , and saturable inductor L 3  and capacitor C 3 . The compressed pulse is delivered from pulse compressor  18  to the excimer laser tube which includes the laser discharge electrodes and other electrically reactive components. 
     A reset signal is applied to terminal  20  from a DC power supply (not shown). The signal causes a current of about 10 amps (A) to flow through L 5 , L 1 , L 2 , and L 3 . This current effectively drives the magnetic cores of these devices from a position in the B-H (hysteresis) loop thereof following a pulse compression, back into one corner of the B-H loop. A sufficient reset is a precondition for obtaining reproducible transition times between one pulse and the next through the pulse-compressor and minimizing jitter between pulses. 
     Considering now problems that would be encountered in trying to drive two excimer lasers, each with a circuit arrangement similar to that of arrangement  10  of  FIG. 1 , one prerequisite for a low jitter time between pulses delivered by the pulse compressor  18  of each is that the charged voltage of storage capacitor C 0  of each must be as reproducible as possible from pulse to pulse. These storage capacitors are each charged in approximately 1 millisecond (ms) via the HSVP, which may be regarded as a regulated current source. The achievable control precision (voltage regulation accuracy) of the high voltage of typical such HSVPs is about ±0.1% of the maximum high-voltage value of the power supply, which is usually about unit of 2.3 kilovolts (kV). A typical controlled value is about 1.6 kV, i.e., well below the maximum. 
     The voltage-time area (the magnetic saturation flux) of transformer cores of stages of pulse compressors  18  is essentially a constant, with only a small drift or variation resulting from a change in temperature of the core material. These variations are sufficiently slow to enable relatively easy correction for example by controlling the relationship of independent discharge-trigger signals of the circuits. The saturation flux (Ψ) of a compressor stage can be represented by the following equation:
 
Ψ= N∫ 2 B   s   dA=∫Udt =const.  (1)
 
wherein N represents the number of turns of the respective compressor stage saturable inductor; B s  is the saturation-induction of the core material used; and A is the magnetically-effective core cross-section.
 
     The required time for saturation of the core, and hence transition to a low-inductive state, is obtained from the integral of Udt (the voltage-time area), wherein U is the voltage over this saturable inductivity, which, in turn, is proportional to the charging voltage at the capacitor C 0 . It follows from this that a variation of this voltage leads directly to a change in the saturation time (the time for the through-connection of the inductances L 5 , L 1 , L 2 , and L 3 ), with the change in time being about 1/U. In the example under consideration, a voltage change of as small as 1 V at capacitor C 0  would lead to a time change of between about 5 and 7 ns for the pulse passage through the entire pulse compressor  18 . 
     Because each of the two lasers to be synchronized has an independent high-voltage power supply unit, relative voltage fluctuations in a range of 4.6 V can occur. This would lead to up to 32-ns fluctuations in the time difference between the light pulses delivered by each of the lasers. This is a random pulse-to-pulse phenomenon and can not be predicted, and accordingly can not be corrected. 
     In theory at least, the above described jitter problem could be rectified by using HVPSs which would allow a pulse to pulse voltage fluctuation (at each C 0 ) of less than about 0.015%. Realization of such power supplies, however, is technologically achievable only with great difficulty and at significant expense. This is because of required high charging power of approximately 50 kilowatts (kW) and charging voltages on the order of 2 kV. There is a need for a solution to the excimer laser synchronization problem that does not require the development of improved power supplies or any other laser components. 
     SUMMARY OF THE INVENTION 
     The present invention is directed to electrical apparatus for energizing first and second gas-discharge lasers. In one aspect the apparatus includes first and second storage capacitors and first and second high-voltage power sources arranged to charge respectively the first and second storage capacitors. First and second pulse-forming circuits are arranged to discharge respectively the first and second storage capacitors. The discharging of the capacitors generates respectively first and second electrical pulses which are delivered to respectively the first and second gas discharge lasers. A switching arrangement is provided and arranged to connect together the first and second storage capacitors after the capacitors are charged for a predetermined time period prior to the discharge of the capacitors by the pulse-forming circuits. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       The accompanying drawings, which are incorporated in and constitute a part of the specification, schematically illustrate a preferred embodiment of the present invention, and together with the general description given above and the detailed description of the preferred embodiment given below, serve to explain principles of the present invention. 
         FIG. 1  schematically illustrates a prior-art arrangement for energizing a pulsed gas discharge laser including a storage capacitor charged by a high voltage power supply, and pulse forming circuitry arranged to discharge the capacitor through a pulse transformer to form an electrical pulse, electrically compress the pulse, and deliver the compressed pulse to the gas discharge laser. 
         FIG. 2  schematically illustrates apparatus in accordance with the present invention including first and second energizing arrangements each similar to the arrangement of  FIG. 1 , and an arrangement for temporarily connecting the storage capacitors of each after the capacitors are charged but before the capacitors are discharged. 
         FIG. 3  is a timing diagram schematically illustrating one example of the operation of the apparatus of  FIG. 2 . 
     
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     Continuing now with reference to the drawings, wherein like features are designated by like reference numerals,  FIG. 2  is an electrical circuit diagram schematically illustrating a preferred embodiment  10  of apparatus in accordance with the present invention for synchronous operating two excimer lasers (not graphically depicted). The lasers are referred to in  FIG. 2  as laser A and laser B. Lasers A and B are energized, individually, by laser pulsing arrangements  10 A and  10 B respectively, each similar to the above-described prior-art pulsing arrangement  10  of  FIG. 1 . 
     Each pulsing arrangement includes a high-voltage power supply  32  charging a storage capacitor C 0  (CO A  and CO B ) via a magnetic isolator  14 . An electrical pulse is generated by commanding IBGT-1, via a trigger-voltage applied to the gate thereof, to discharge capacitor C 0  through a pulse transformer L 5  (as discussed above). The magnetic pulse compressor  18  temporally compresses the pulse, and delivers the compressed pulse to the laser discharge-electrodes. Common features of the arrangements  10 A and  10 B are identified by suffixes A and B applied to the corresponding reference numeral. Apparatus  30  is controlled software in a PC or the like (not shown) which provides all control signals referred to hereinbelow. 
     As discussed above, absent any pulse-to-pulse charging-voltage differences between storage capacitors CO A  and CO B , optimal synchronization of the output of the lasers, and corresponding minimization of jitter, could be accomplished by taking into account the different transit-times for a pulse generated by discharge of a capacitor, and by synchronizing pulse-trigger signals Trigger-A and Trigger-B. 
     In apparatus  30 , fluctuations of pulse-to-pulse charging-voltage differences are minimized, as summarized above, by connecting capacitors CO A  and CO B , together, after the capacitors are charged, for a short period before a pulse is triggered by either Trigger-A or Trigger-B. The connection is established by a switching arrangement  40  including IGBT modules  42 A and  42 B, which are driven by drivers  44 A and  44 B respectively. An IGBT protection and control circuit  46  generates digital signals for the drivers, responsive to a digital connect signal from the software controlling the apparatus. Circuitry  46  also monitors the voltages of capacitors and is arranged to prevent turning on IGBTs  42 A and  42 B if the voltage difference between the capacitors exceeds a predetermined level, for example 100 V. This serves to protect the IGBTs in the event that one of HSVPs malfunctions, and the corresponding capacitor is not charged or not sufficiently charged. Circuitry  40  can be referred to as an “equilibrium switch” or EQUI-Switch. 
     IGBTs  42 A and  42 B are connected as depicted in  FIG. 2  in an anti-serial manner. This provides that the IGBTs are able to switch both positive and negative polarities of the capacitors. This also provides that lasers A and B can be operated separately from each other, and be independent of the relative adjustment of power supplies HVPS-A and HVPS-B. 
     The power supplies are regulated such that one of the capacitors, for example capacitor CO A , is initially charged to a higher voltage than the other (CO B ). In general terms, the voltage difference must be high enough, so that under worst condition the difference is still higher than sum of the flux voltage of one IGBT switch plus the flux voltage of the internal freewheeling diode of the other (anti-serial) IGBT and the residual voltage difference at which the HVPS with the lower voltage takes advantage of the fluctuation upward and the power supply unit with the higher voltage takes advantage of the fluctuation downward, i.e., the voltage-regulation accuracy of the power supplies. As noted above, this is about 4.6 V (±2.3 V) in the example under consideration. Only under this condition will there always be charge equalization, with the equalization current always flowing in the same direction. The voltage difference, however, should not be too high, otherwise the equalization may take longer than is practical (&gt;100 μs in this example) or the equalization current may be too high. A voltage about 15 V higher has been determined to be adequate, in the example under consideration. 
     The impedance (R) of the connection between CO A  and CO B  is chosen (if necessary, by putting additional resistance in series with IGBTs  42 A and  42 B) to satisfy a condition
 
 R≧ 2*( L/C ) 0.5   (2)
 
where L is mainly cable inductance and
 
 C=C 0 A   *C 0 B /( C 0 A   +C 0 B )  (3)
 
     The resulting equalizing current of several tens of amps ensures that voltages of capacitors CO A  and CO B  adjust aperiodically, within approximately 50 microseconds (μs), up to the flux voltages of the IGBT operated in the forward current direction and of the internal freewheeling diode of the other respective IGBT. 
     Although, as noted above, a residual voltage determined by the regulation accuracy of the HVPSs always remains as the difference in the two charging capacitor voltages, it is reproducible and does not contribute to the temporal jitter. Because of this, the charge voltages of CO A  and CO B  still fluctuate absolutely by about ±2.3 V, but relative to each other by less than 200 mV. This means that, although the gas discharges and, as a result, the light pulses of lasers A and B jitter against the discharge trigger signal of each, the lasers achieve a temporal stability in the nanosecond range relative to each other. Realizable values lie between about 2 ns and 5 ns peak-peak. Accordingly, the temporal shape of the two spatially and temporally overlapped light pulses, largely corresponds to the temporal shape of the individual pulses. This provides that interaction of the overlapped pulses with a material being processed thereby takes place in the same manner as for any one of the individual pulses having twice the energy. 
     A description of the relative timing of signals operating apparatus  30  as discussed above is next set forth with reference to the timing diagram of  FIG. 3  and with continuing reference to  FIG. 2 . As noted above, these signals are generated or triggered by control software for apparatus  30 . In  FIG. 3 , with an exception of the connection signal, all signals or values are specific to one of the lasers, here, arbitrarily selected as laser A. Signals and values for the other laser will temporally evolve in the same manner. The evolution time of the diagram of  FIG. 3  is slightly greater that one pulse-repetition period, here, assumed to be greater than about 1.67 milliseconds (ms) representative of a pulse repetition frequency of 600 Hz or less. 
     The control software generates a period trigger signal at time t 0 , by which all others are timed. At time t 0 , the inhibit signal (Inhibit A) applied to magnetic isolator  14 A goes from low to high, putting the isolator in a low impedance state to facilitate charging. At this time also, a signal HVA commands power supply HVPS-A to charge capacitor CO A  to the predetermined voltage for that capacitor. The capacitor is nominally charged at a time t 1 , but charging continues to a time t 2  to take into account possible pulse-to-pulse differences in charging time. Values for the period t 0  to t 1  and t 1  to t 2  consistent with the example under consideration are less than or equal to about 1040 microseconds (μs) and 100 μs respectively. At time t 2  the inhibit signal goes from high to low, putting the magnetic isolator in a high impedance state to effectively isolate capacitor CO A  from power supply HVPS-A. 
     A relatively short time after time t 2 , for example, about 10 μs after, the connect signal goes from low to high, closing IGBTs  42 A and  42 B (the EQUI-Switch) so that the above-described voltage equalization between capacitors CO A  and CO B  can take place. A relatively short time before time t 3  (here again about 10 μs), the connect signal goes from high to low opening EQUI-Switch and isolating the capacitors from each other so that capacitors can be independently discharged. At time t 3 , the trigger signal closes IGBT-1A for a period long enough to discharge capacitor CO A , an electrical pulse (not shown) is generated and compressed, and corresponding light output pulse is delivered from the laser a few microseconds later. During a recovery period between times t 3  and t 4 , after IGBT-1A is re-opened the voltage of capacitor CO A  jumps up slightly, due to charging by reflected energy from the discharge due to less than perfect impedance matching, then drifts gradually down to about the original uncharged value by time t 5  at which time a new sequence of signals is triggered. Here, it should be noted that for a PRF of 600 Hz the time period between t 4  and t 5  would be relatively short. However, recharging could actually start at time t 4 . 
     A reason for closing the EQUI-Switch shortly after time t 3  and opening the EQUI-switch shortly before time t 3  is that the EQUI-Switch is common to both lasers. The difference in the EQUI-Switch closed time (about 100 μs) and the period t 3 −t 2  allows for the relative trigger times of the lasers to be varied to compensate for any above-discussed relative drift in pulse-propagation time through pulse-compression circuits  18 A and  18 B, thereby optimizing temporal overlap of the corresponding light pulses. 
     It is emphasized, here, that the embodiment of the present invention described above and circuitry and values used are merely one example and should not be construed as limiting the present invention. Those skilled in the electrical arts, from the description of the present invention provided above, may devise other circuitry for providing the inventive voltage-equalization function without departing from the spirit and scope of the present invention. Further, while the present invention has been described in terms of synchronizing the output of two lasers with independent pulsing arrangements, the invention could be extended to synchronizing three or more lasers with independent pulsing arrangements. By way of, example, three lasers with independent pulsing arrangements could be synchronized using two of the EQUI-switch arrangements described herein. 
     In summary, the present invention is described above in terms of a preferred embodiment. The invention however is not limited to the embodiment described herein. Rather the invention is limited only by the claims appended hereto.

Technology Category: h