Source: http://www.google.com/patents/US20060209894?dq=5636223
Timestamp: 2017-05-23 18:57:12
Document Index: 275701099

Matched Legal Cases: ['art 150', 'art 180', 'art 150', 'art 150', 'art 150', 'art 210']

Patent US20060209894 - Adaptive Allocation For Variable Bandwidth Multicarrier Communication - Google PatentsSearch Images Maps Play YouTube News Gmail Drive More »Sign inPatentsData is distributed among the channels of an asynchronous data subscriber loop (ADSL) communications system in accordance with an adaptive algorithm which from time to time measures the signal to noise ratio of the various channels and finds a margin for each channel dependent on achievement (where possible)...http://www.google.com/patents/US20060209894?utm_source=gb-gplus-sharePatent US20060209894 - Adaptive Allocation For Variable Bandwidth Multicarrier CommunicationAdvanced Patent SearchTry the new Google Patents, with machine-classified Google Scholar results, and Japanese and South Korean patents.Publication numberUS20060209894 A1Publication typeApplicationApplication numberUS 11/422,810Publication dateSep 21, 2006Filing dateJun 7, 2006Priority dateJun 12, 1996Also published asUS6798735, US7817532, US8369275, US8767698, US20050083972, US20110019751, US20130155870Publication number11422810, 422810, US 2006/0209894 A1, US 2006/209894 A1, US 20060209894 A1, US 20060209894A1, US 2006209894 A1, US 2006209894A1, US-A1-20060209894, US-A1-2006209894, US2006/0209894A1, US2006/209894A1, US20060209894 A1, US20060209894A1, US2006209894 A1, US2006209894A1InventorsMarcos Tzannes, George Kechriotis, Pui WuOriginal AssigneeAware, Inc.Export CitationBiBTeX, EndNote, RefManPatent Citations (32), Referenced by (34), Classifications (6), Legal Events (4) External Links: USPTO, USPTO Assignment, EspacenetAdaptive Allocation For Variable Bandwidth Multicarrier Communication
US 20060209894 A1Abstract
Data is distributed among the channels of an asynchronous data subscriber loop (ADSL) communications system in accordance with an adaptive algorithm which from time to time measures the signal to noise ratio of the various channels and finds a margin for each channel dependent on achievement (where possible) of a given bit error rate and a desired data transmission rate. The margin distribution is achieved by augmenting the constellation signal to noise ratio to enhance computational efficiency and allow redetermination of bit allocation tables during transmission as necessary. Pairs of bit allocation tables are maintained at the transmitter and receiver and one table of each pair at the transmitter and receiver is updated while the other pair is in use for controlling communication. Images(8) Claims(3)
CROSS-REFERENCE TO RELATED APPLICATIONS [0001] This application is a continuation of U.S. patent application Ser. No. 10/768,138, filed Feb. 2, 2004, now pending, which claims the benefit of and priority to U.S. patent application Ser. No. 09/421,835, filed Oct. 20, 1999, now U.S. Pat. No. 6,798,735, issued Sep. 28, 2004, which claims the benefit of and priority to U.S. patent application Ser. No. 08/873,421, filed Jun. 12, 1997, now U.S. Pat. No. 6,072,779, issued Jun. 6, 2000, which claims the benefit of and priority to U.S. Provisional Application Ser. No. 60/019,637 filed Jun. 12, 1996, all of which are incorporated herein by reference in their entirety. TECHNICAL FIELD [0002] This application relates to the field of electronic communication and more particularly to the field of multiband digital signal communication. BACKGROUND OF THE INVENTION [0003] Conventional multicarrier digital communication is a technique for transmitting and receiving digital signals using a plurality carriers (subchannels) having different frequencies. Each of the subchannels is used to communicate a different portion of the signal. The transmitter divides the signal into a number of components, assigns each component to a specific one of the carriers, encodes each of the carriers according to the component assigned thereto, and transmits each of the carriers. The receiver decodes each received carriers and reconstructs the signal. [0004] The maximum amount of information that can be encoded onto a particular sub-carrier is a function of the signal to noise ratio of the communication channel with respect to that subcarrier. The signal to noise ratio of a communication channel can vary according to frequency so that the maximum amount of information that can be encoded onto one carrier may be different than the maximum amount of information that can be encoded onto another carrier. [0005] Bit loading is a technique for assigning bits to subchannels according to each sub-channel's signal to noise ratio. A bit loading algorithm provides a bit allocation table that indicates the amount of information (in bits) that is to be encoded on each of the carriers. That is, for a multicarrier communication system with J carriers, a bit allocation table BU] indicates, for each j=1 to J, the amount of information that is to be encoded onto each of the J carriers. [0006] Shaping the transmission to match the channel characteristics is known. For example, a technique known as “water pouring” was introduced by Gallager in 1968 (“Information Theory and Reliable Communication”, page 389) and by Wozencraft in 1965 (“Principles of Communication Engineering”, pp. 285-357). Water pouring involves distributing the energy of the transmission signal according to the channel frequency response curve (a plot of the signal to noise ratio as a function of frequency). The frequency response curve is inverted and the available signal energy (the “water”) is “poured” into the inverted curve so that more of the energy is distributed into those portions of the channel having the highest signal to noise ratio. In a multicarrier system in which the transmission band is divided into numerous subchannels, throughput can be maximized by putting as many bits in each subcarrier as can be supported given the “water pouring” energy and a desired error rate. [0007] Other techniques for allocating bits among carriers of a multicarrier signal are known. U.S. Pat. No. 4,731,816 to Hughes-Hartogs discloses a bit loading scheme where one bit at a time is incrementally added to each subcarrier until a maximum rate is achieved. Subcarriers that require the least amount of additional power to support an additional bit are selected first. [0008] U.S. Pat. No. 5,479,477 to Chow et al. discloses a bit loading scheme that is capable of either maximizing the throughput or maximizing the margin for a particular target data rate. Unlike Hughes-Hartogs, Chow et al. determines the bit loading table one carrier at a time (rather than one bit at a time). In Chow et al., all the carriers are sorted in descending order according to the measured signal to noise ratio. The initial subchannels that are selected are the ones capable of carrying the most bits. Using the Chow et al. scheme to maximize the data rate provides a bit loading table similar to that provided by the Hughes-Hartogs algorithm. [0009] In order for the receiver to correctly interpret the received data, both the transmitter and the receiver must use the same bit loading table. When the bit loading algorithm is performed during the initialization phase of communication, the resulting bit allocation table is communicated between the transmitter and receiver to ensure that both the transmitter and the receiver are using the same bit loading table. However, in the event that the communication channel signal to noise ratio characteristics change during communication, it may be necessary to update/change the bit allocation table to more appropriately match the transmission with the channel characteristics. However, when the bit allocation table is changed, it is necessary to synchronize use of the new table with both the transmitter and the receiver. If the transmitter and the receiver use different bit allocation tables at any time, the communications link will suffer significant errors in those subchannels in which the bit allocation tables do not agree. [0010] In addition, determining a new bit allocation table can be time consuming, especially if the bit loading algorithm is computationally intensive, such as that disclosed by Hughes-Hartogs where the bit allocation table is constructed one bit at a time. If the bit allocation table is to be calculated many times during communication between the transmitter and receiver, then spending a relatively long amount of time recalculating the bit allocation table (and hence not communicating data) is undesirable. [0011] One solution is to simply not change the bit loading table after initialization. However, this may be unacceptable in cases where the communication channel signal to noise ratio changes during data transmission. Accordingly, it is desirable to be able to determine a bit loading table relatively quickly and to be able to synchronize use of the new table by the transmitter and the receiver. SUMMARY OF THE INVENTION [0012] In accordance with the present invention, a pair of bit allocation tables are maintained at both the transmitter and the receiver. These tables are updated as needed, using measurements of the signal to noise ratio performed on known data transmitted to the receiver in a control flame separate from the data frame. The transmitter signals the receiver as to which of the two tables is to be used for subsequent communication. Preferably, this is done by transmitting a flag from the transmitter to the receiver at some point during the data transmission; this causes the receiver to thereafter switch the bit loading table it is using for communication to synchronize with the corresponding table at the transmitter. [0013] In the preferred embodiment of the invention, although the invention is not restricted thereto, 69 “frames” of 245.5 microseconds duration each are used to form a “superframe” of 16.94 milliseconds. The first frame of each superframe comprises a control frame that is used to transmit a standard (known) data set from the transmitter to the receiver; the remaining frames contain data. The receiver measures the signal to noise ratios of the received data in this frame for each of the channels and uses this to calculate channel bit allocations for subsequent data transmissions. In practice, it has not been found necessary to calculate the signal to noise ratios for each and every superframe, although this can, of course, be done. Rather, we have found it sufficient for most data transmissions to measure the signal to noise ratios of the channels over several frames, average them, update the bit allocation tables based on the resultant values, and use the bit allocations tables so determined over hundreds or thousands of subsequent frames. [0014] The bit allocation table updating is performed by comparing the measured signal to noise ratio (SNR) in each channel with a constellation signal to noise ratio SNR[cj], that has been augmented by a trial noise margin M, SNRa[cj]=SNR[cj]+M. The constellation signal to noise ratio, SNR[cj], specifies the number of bits cj (“constellation size”) that can be transmitted over a channel j given a specific signal to noise ratio SNRj, where cj may vary, for example, from 1 to 15. The value of the margin M is dependent on the difference between the amount of data (i.e., number of bits) that can be transmitted across the channels in accordance with the augmented constellation signal to noise ratio SNRa[cj] and the amount that is desired to be transmitted (the “target data rate”), N. The value of this margin is varied in order to optimize it for the particular communication conditions as manifested by the measured signal to noise ratios, SNRj. [0015] In particular, the total number of bits that may be transmitted over J channels, each characterized by signal to noise ratio SNRj, is N max = ∑ j = 1 J c j , where the respective cj are determined from the measured signal to noise ratios, SNRj. See, for example, “Digital Communications” by John G. Proakis, pp. 278ff for channel capacity calculations for quadrature amplitude modulation (QAM) systems, the preferred form of transmission for this invention. Preferably, the channel capacity calculations are performed in advance and stored in the form of lookup tables for rapid access. In the preferred embodiment described herein, the margin M is determined as M=(10/J)*(Nmax−N). The augmented constellation signal to noise ratio is then given by SNRa[cj]=SNR[cj]+M, and this value is used to determine (e.g., by table lookup as described above) the number of bits that can be transmitted over a channel. By augmenting the constellation signal to noise ratio, SNR[cj], rather than the channel signal to noise ratio, SNRj, fewer additions are required, since the range of constellation sizes (e.g., cj=1 . . . 15) is typically smaller than the range of channels (e.g., j=1 . . . 256). [0016] As long as the amount of data that can be transmitted over the channels in a given interval differs (as determined by the calculations just described) from the amount of data desired to be transmitted in that interval, i.e., Nmax≠N, and assuming that certain other exit conditions have not been satisfied, the receiver cycles through a loop that repeatedly adjusts the margin M and recalculates Nmax. To do this, the receiver sets a high margin threshold MH and a low margin threshold ML. During those superframes in which the bit allocation table is to be recalculated, the high threshold and low threshold margins are initialized to either a first state (ML=0, MH=(10/J)*[Nmax−N]) or a second state (MH=0, MH=(10/J)*[Nmax−N]) dependent on whether Nmax is greater than N or less than N. [0017] Thereafter, in each iteration, either the high or the low margin is adjusted in the search for the condition in which Nmax=N. Specifically, at the beginning of subsequent (non-initialization) iterations, the margin is set to the average of the high and low margin thresholds, M=(MH+ML)/2, and the augmented constellation signal to noise ratio SNRa[cj], the bit allocation table B[j], and the calculated capacity Nmax are determined. [0018] If the calculated capacity exceeds the desired capacity, i.e., Nmax>N, the receiver increases the low margin threshold margin to M, i.e., it sets ML=M. If the calculated capacity is less than the desired capacity, i.e., Nmax<N, the receiver decreases the high threshold, i.e., it sets MH=M. The iteration then repeats. [0019] The receiver exits from the loop on the occurrence of any of several conditions. A first occurs when it is determined that Nmax=N. This is the desired solution, and represents an optimum equal distribution of margin over the communication channels. A second occurs when the test condition (Nmax−N) is diverging. A third occurs when the desired equality is not achieved after a defined number of iterations. In one system implemented according to the preferred embodiment described herein, we have found a limit of 16 iterations sufficient.
BRIEF DESCRIPTION OF THE DRAWINGS [0020] FIG. 1 is a schematic diagram of an ADSL communications system showing bit allocation tables in accordance with the present invention; [0021] FIG. 2 is a diagram of control and data frames as used in connection with the present invention; [0022] FIG. 3 is a graph illustrating a multicarrier communication system. [0023] FIG. 4 is a graph illustrating signal-to-noise ratio as a function of frequency. [0024] FIG. 5 is a graph illustrating bit loading and margin for a multicarrier communication system. [0025] FIG. 6 is a flow chart illustrating a bit loading algorithm for a multicarrier communication system. [0026] FIG. 7 is a flow chart illustrating initialization for the bit loading algorithm of FIG. 6. [0027] FIG. 8 is a flow chart illustrating operation of a receiver software for calculating, modifying, and synchronizing a change in a bit allocation table used in a multicarrier communication system. DETAILED DESCRIPTION OF AN ILLUSTRATIVE EMBODIMENT [0028] In FIG. 1, a transmitter 10 for use in asynchronous data subscriber loop (ADSL) communications has first and second bit allocation tables 12 and 14 for use in assigning data to a plurality of channels for transmission to a remote receiver 16 which has corresponding bit allocation tables 20 and 22. The tables operate in pairs under control of a table controller 24 at the transmitter. In accordance with ADSL practice, a digital signal s(t) to be transmitted to a receiver is distributed over a plurality of channels f1, f2, . . . fj, in accordance with channel allocation assignments stored in the bit allocation tables. In particular, the tables B[j] define, for each channel j, the number of bits that can reliably be transmitted over a particular channel at a given bit error rate at the specific signal to noise ratio measured for that channel. These tables are determined as described in detail herein, and may vary from time to time during the course of a transmission. [0029] At any given time, a single table, e.g., table 12, is used for transmission at the transmitter, and a corresponding table, e.g., table 20, is used for reception at the receiver. These tables are images of each other, i.e., contain the same data, and are used in pairs, so that reliable communication can occur. Similarly, tables 14 and 22 are images of each other and are used in pairs. [0030] A table control unit 24 at the receiver controls the formation of the bit allocation tables 12, 14, 20, and 22. It measures the signal to noise ratio on each of the channels f1, f2, . . . fj, compares the measured values with predetermined values defining the bit capacity of a channel at given signal to noise values, augmented with noise margins as described herein, and thus determines the bit allocation for each channel. The allocations so defined are stored in the tables 20 and 22 at the receiver. They are also transmitted back to the transmitter, e.g., via a control channel 26, and are there stored as the tables 12 and 14, respectively. After initial loading, the transmission is advantageously arranged such that only updated tables are transmitted back to the transmitter. [0031] At the transmitter 10, a table switch unit 28 selects which of the two table pairs (12, 20; 14, 22) are to be used in a given transmission and reception. Typically, a given pair will continue in use until the communication conditions change sufficiently that the bit allocations among the channels change. At that time, a new table must be formed at the receiver, and communicated to the transmitter. When this occurs, the table switch unit 28 typically will switch to the new table for subsequent transmissions. When it does so, it transmits a flag to the receiver that indicates that a switch to the alternative pair is to take place. This switch will usually be made effective as of the next superframe, but may, by prearrangement with the receiver, be made effective at some agreed upon point after that. [0032] FIG. 2 is a diagram of a superframe 30. It is formed from a control frame 32 and a number of data frames 34. During the control frame interval, the transmitter sends to the receiver a known signal from which the receiver can measure the signal to noise ratio of each of the channels in order to calculate the bit allocations. The remaining frames of the superframe comprise data frames for the transmission of the desired data. In a preferred embodiment of the invention, there are one control frame and 68 data frames, each of 245.5 microsecond duration, for a superframe time of 16.94 milliseconds. [0033] Referring to FIG. 3, a graph 100 illustrates multicarrier signal transmission. The graph 100 has a horizontal axis 102 representing frequency wherein lower frequencies are toward the left side of the axis 102 while higher frequencies are toward the right side of the axis 102. The graph 100 illustrates that a multicarrier signal, incorporating J discrete carrier signals, is transmitted via carriers at frequencies f1, f2, . . . fj. [0034] Each of the carriers shown in the graph 100 is capable of transmitting a certain number of bits of information. Accordingly, the total number of bits transmitted via the multicarrier signal is the sum of the number of bits that can be transmitted by each of the carriers. For example, if each of the carriers can transmit three bits of information, then the signal shown in the graph 100 can transmit a total of J*3 bits of information. [0035] In a preferred embodiment, each of the carriers transmits information using quadrature amplitude modulation (QAM), a conventional digital signal encoding technique where different combinations of amplitude and phase of each carrier signal represent different digital values. For example, a carrier signal can be encoded using two different possible amplitudes (A1 and A2) and two different possible phases (P1 and P2) so that the carrier can represent one of four possible values: a first value when the carrier signal has amplitude A1 and P1, a second value corresponding to a combination A1 and P2, a third value corresponding to a combination A2 and P1, and a fourth value corresponding to a combination A2 and P2. The various combinations of amplitude and phase for a given carrier signal is called a “constellation”. Note that the number of bits that can be transmitted via a particular carrier is a function of the maximum possible constellation size for that carrier. [0036] For each carrier, the maximum size of the constellation, and hence the maximum number of bits that can be transmitted via that carrier, is a function of the signal to noise ratio (SNR) of the communication channel and is a function of the desired bit error ratio (BER). The BER is the number of single bit transmission/reception errors per the total number of bits transmitted. Increasing the number of discrete amplitudes and/or phases associated with a particular carrier (i.e., increasing the constellation size) increases the likelihood of bit errors. The BER increases with increasing constellation size because, as the number of discrete amplitudes and/or phases increases, the magnitude of the difference between discrete phases and/or amplitudes decreases and hence the ability of the receiver to distinguish between different phase and/or amplitude values decreases. [0037] The relationship between BER and SNR is well-known in the art of multicarrier communication. Tables are available that show the minimum SNR that can support a BER of a fixed amount or less for a given constellation size. For example, the table shown below, SNR[cj], a constellation signal to noise ratio, indicates the minimum SNR needed to transmit a constellation having the indicated size in order to obtain an expected BER of 10−7 (i.e., an error of one bit per every 107 bits that are transmitted.) Note that as the constellation size increases, the minimum required SNR also increases. Constellation size c (in bits) SNR requirement 2 14 dB 3 19 dB 4 21 dB 5 24 dB [0038] Referring to FIG. 4, a graph 110 illustrates a relationship between SNR and frequency for a communication channel transmitting a multicarrier signal having carriers between frequencies f1, and fj. A vertical axis 112 of the graph 110 represents SNR. A horizontal axis 114 of the graph 110 represents frequency in a manner similar to that illustrated in connection with the horizontal axis 102 of the graph 100 of FIG. 3. [0039] A plot 116 shows the relationship between SNR and frequency for the frequencies between f1, and fj, the lowest and highest (respectively) carrier frequencies for the multicarrier frequency signal. The plot 116 illustrates that the SNR varies according to frequency so that, for example, the SNR at frequency fm is lower than the SNR at frequency fn. Based on the table shown above, it is possible that, for a given BER, the constellation size supported by the carrier frequency fm is smaller than the constellation size supported by the carrier frequency fn. [0040] Referring to FIG. 5, a graph 120 uses a plot 122 to illustrate a hypothetical relationship between SNR and frequency. The graph 120 is similar to the graph 110 of FIG. 4. The vertical axis of the graph 120, which represents SNR, has superimposed thereon the SNR requirement numbers from the table, shown and discussed above, that relates minimum SNR requirements with constellation size for a BER of 10−7. The graph 120 shows that an SNR of 14 dB is required to support a constellation size of two bits and that SNR's of 19, 21, and 24 are required to support constellation sizes of three, four, and five bits, respectively. Based on this, it is possible to use the plot 122 to determine a maximum constellation size for each of the carrier frequencies between f1, and fj. For example, the plot 122 shows that any carrier frequencies between f1, and fa can support a maximum constellation size of four bits since all portions of the plot 122 between f1, and fa are greater than 21 dB (the minimum required SNR to support a constellation size of four bits), but less than 24 dB (the minimum SNR for five bits). No carrier frequencies between f1, and fa can support a constellation size of five bits at the BER used to generate the minimum SNR requirements. [0041] The portion of the plot 122 between fa and fb is shown in FIG. 5 as being greater than 24 dB. Accordingly, carrier frequencies between fa and fb can support a maximum constellation size of at least five bits. Similarly, carrier frequencies between fb and fc will support a maximum constellation size of four bits; carrier frequencies between fc and fd will support a maximum constellation size of three bits; carrier frequencies between fd and fe will support a maximum constellation size of two bits, and carrier frequencies between fe and fj will support a maximum constellation size of three bits. [0042] The difference between the minimum required SNR and the actual transmission channel SNR is called the “margin”. For example, the plot 122 shows that if four bits are used at the carrier frequency f1, the carrier frequency at f1 will have a margin 124 somewhat greater than zero since the SNR at f1 is shown in FIG. 5 as being greater than the minimum SNR requirement of 21 dB. Similarly, it is possible to use less than the maximum supported constellation size at a particular carrier frequency; For example, although the plot 122 shows that a carrier at the frequency fa will support a constellation size of five bits (since the SNR at fa is 24 dB),. it is possible to encode the carrier at the frequency fa with only three bits. In that case, the margin at the frequency fa is the difference between the transmission channel SNR at fa (24 dB) and the SNR required to support a constellation of three bits at frequency fa (19 dB). Accordingly, the margin at frequency fa is 5 dB. [0043] In instances where the multicarrier signal is used to transmit the maximum number of data bits, then the SNR of the communication channel is first measured and then each carrier is set to the maximum supported constellation size. However, in many applications, the multicarrier signal is used to transmit less than the maximum possible number of bits. In those cases, it is advantageous to maximize the overall margin of the signal to thus reduce the error rate. This can be illustrated by a simple example: [0044] Assume a two-channel multicarrier signal has a maximum constellation size of five bits for the first carrier and four bits for the second carrier. Further assume that it is desirable to use the signal to transmit six bits. One way to allocate the bits among the two carriers is to use the first carrier to transmit five bits and the second carrier to transmit one bit. In that case however, the margin for the first carrier is relatively small while the margin for the second carrier is relatively large. There will be many more errors for bits transmitted via the first carrier than bits transmitted via the second carrier and, since most of the bits are being transmitted via the first carrier anyway, then the overall error rate of the signal, while below the target BER, is still higher than it has to be in this case. A more advantageous way to allocate the bits might be to allocate three bits to each of the two carriers. In that case, both of the carriers operate with a relatively large margin and the overall error rate of the signal is reduced. [0045] Of course, in many multicarrier communication applications, there are hundreds of carriers and hundreds to thousands of bits that are transmitted. In addition, it is necessary to allocate the bits in a relatively rapid manner since time spent allocating bits is time not spent communicating information. Furthermore, it may be necessary to reallocate the bits during communication if the channel transmission characteristics change dynamically. [0046] Referring to FIG. 6, a flow chart 150 illustrates a technique for allocating bits among carriers of a multicarrier signal. Processing begins at a first step 152 where various quantities used to allocate the bits are initialized. These quantities include MH, the high-bound for the margin, ML, the low-bound for the margin, and k, an iteration counter which is described in more detail below. Following step 152 is a step 154 where the margin, M, is calculated by averaging MH and ML. [0047] Following step 154 is a step 156 where a table indicating required SNR for various constellation sizes, RSNR[c], is calculated. RSNR[c] is a table having entries equal to the sum of the margin, M, and the minimum SNR requirements that can support a constellation of size c, and thus comprises an augmented constellation signal to noise ratio, SNRa[cj]=SNR[cj]+M. Following step 156 is a step 158 where a bit table, B[j], is calculated. B[j] is a table of the maximum number of bits that can be allocated to each of the carriers f1, . . . fj, given the values stored in RSNR[c]. The maximum number of bits are allocated for each carrier in a manner similar to that discussed above in connection with FIG. 5. [0048] Following step 158 is a step 160 where a value Nmax is calculated. Nmax represents the maximum number of bits that can be transmitted on the channel and is determined by summing all of the values in the table B[j]. Since the table B[j] contains the maximum number of bits that can be transmitted for each carrier based on the minimum required SNR for each constellation size plus the calculated margin, then Nmax represents the maximum number of bits that can be transmitted on the channel wherein each of the carriers has a margin of at least M. [0049] Following the step 160 is a test step 162 which determines if Nmax equals N where N is the number of bits that are to be transmitted using the multicarrier signal. If Nmax does in fact equal N, then processing is complete and the bit table B[j] represents an allocation of bits among the carriers of the multicarrier signal wherein each carrier will have a margin at least as large as M. [0050] If it is determined at the test step 162 that Nmax does not equal N, then processing transfers from the test step 162 to a test step 164. Note that if N is less than Nmax, then the margin can be increased (in order to decrease Nmax) in the next iteration. Similarly, if N is not less than Nmax, then the margin is too large and needs to be decreased in the next iteration. If it is determined at the test step 164 that N is less than Nmax, the control transfers from the test step 164 to a step 166 where ML, the low-bound on the margin, is set equal to M. Setting ML equal to M effectively increases ML, causing an increase in the value of the margin, M, that will be calculated on the next iteration at the step 154. [0051] Conversely, if it is determined at the step 164 that N is not less than Nmax, then control transfers from the step 164 to a step 168 where MH, the high-bound on the margin is set equal to M. This effectively decreases the value of MH, thus causing the value of M to decrease when M is calculated at the step 154 on the next iteration. [0052] Control transfers from either the step 166 or step 168 to a step 170 where the iteration counter, k, is incremented. Following the step 170 is a test step 172 which determines if the iteration counter is less than the maximum allowable value for the iteration counter, Kmax . The iteration counter, k, is used to ensure that the algorithm will terminate after a certain number of iterations even if the terminating condition at the step 162 (i.e., Nmax=N) is never met. In a preferred embodiment, Kmax equals 16. [0053] If it is determined at the test step 172 that k is not less than Kmax, then control transfers from the step 172 to a step 174 where the remaining bits are either removed or added to the bit table, B[j], as appropriate. Bits are added or removed at the step 174 in a random or pseudo random manner so that the sum of all allocated bits in the table B[j], equals N, the number of bits that are to be transmitted via the multichannel signal. Note that in this instance, there is no guarantee that each of the carriers has a margin of at least M. The step 174 is simply executed in order to finalize the allocation process if the algorithm is unable to meet the termination condition at the step 162. [0054] If it is determined at the test step 172 that the iteration counter, k, is less than the predetermined maximum value for the iteration counter, then control transfers from the step 172 to a test step 176 which determines if the algorithm is diverging, i.e., if (Nmax−N) is increasing. It is desirable for the algorithm to converge so that the value of Nmax, gets closer to the value of N with each iteration because the algorithm terminates when Nmax equals N at the test step 162. However, if it is determined at the test step 176 that the value of Nmax is actually getting farther from the value of N with each iteration, then control transfers from the step 176 to the step 174 where the remaining bits are distributed randomly among the values in the table B[j], as discussed above, after which processing is complete. [0055] If it is determined at the test step 176 that the algorithm is not diverging, then control transfers from the step 176 back to the step 154 where the margin is calculated for the next iteration. The margin calculated at the subsequent iteration 154 will either be less than or greater than the margin calculated on the previous iteration, depending upon whether N was less than Nmax or not at the test step 164, as discussed above. [0056] Referring to FIG. 7, a flow chart 180 illustrates in detail the initialization routine for the step 152 of the flow chart 150 shown in FIG. 6. The initialization routine is entered and processing begins at a step 182 where the transmission characteristics of the channel are measured to determine the signal-to-noise ratio at each of the carrier frequencies of the multicarrier signal. As discussed above in connection with FIGS. 4 and 5, the transmission channel signal-to-noise ratio may be a function of frequency. Measuring the channel transmission characteristics at the step 182 is discussed in more detail hereinafter. [0057] Following the step 182 is a step 184 where the minimum required signal-to-noise ratio table, SNR[c], is initialized. As discussed above, for a given bit error ratio (BER), the minimum required SNR for each constellation size, c, can be determined via conventional calculations known in the art or by looking up the values in a textbook. Following the step 184 is a step 186 where the bit table, B[j], is calculated. Calculation of the bit table at the step 186 is similar to calculation of the bit table at the step 158 discussed above in connection with the flow chart 150 of FIG. 6, except that the unaugmented SNR table is SNR[cj] used at the step 186 rather than the RSNR table which is used at the step 158. Using the SNR table at the step 186 effectively calculates the bit table, B[j], with a margin of zero. Following the step 186 is a step 188 where Nmax is calculated. The step 188 is similar to the step 160 discussed above in connection with the flow chart 150 of FIG. 6; Nmax is simply the sum of all the entries in the bit table, B[j]. [0058] Following the step 188 is a step 190 where it is determined if Nmax equals N. If Nmax does equal N at the step 190, then processing is complete for the entire algorithm (not just the initialization portion) since the channel will only support Nmax bits of transmission. That is, if Nmax equals N at the step 190, there is no point in continuing with the algorithm and calculating a margin since, by default, the channel can transmit no more than N bits. [0059] If it is determined at the test step 190 that Nmax does not equal N, then control transfers from the step 190 to a test step 192 where it is determined if N is less than Nmax. Note that if N is not less than Nmax at the step 192, then the channel will not support transmission of N bits at the BER used to construct the SNR table at the step 184. That is, the bandwidth of the channel is too low. However, in this case, the algorithm can continue by calculating a negative margin and simply proceeding to maximize the negative margin so that, although the BER that will be achieved will exceed the desired BER, it is still minimized given the requested data rate. In another embodiment, the algorithm can terminate at this point and indicate that the bits cannot be allocated. In yet another embodiment, the algorithm can be rerun using a higher BER and (presumable) lower minimum SNR requirements for the various constellation sizes. [0060] If it is determined at the step 192 that N is not less than Nmax (i.e., the system will be operating with a negative margin) then control transfers from the step 192 to a step 198 where the low-bound on the margin ML, is set to zero. Following the step 198 is a step 200 where the high-bound on the margin is set using the formula MK=(10/J*)(Nmax−N). Note that, however, in this case the high-bound on the margin will be set to a positive value at the step 200 because Nmax−N will be a positive number. [0061] Following either the step 200 or the step 196, control transfers to a step 202 where the iteration counter that is used to terminate the algorithm after a predetermined number of iterations is set to one. Following the step 202, the initialization routine is exited so that the remaining processing, as discussed above in connection with FIG. 6, can continue. [0062] The formula used to set ML at the step 196 and to set MH at the step 200 provides upper and lower bounds of the margin such that the algorithm converges in a reasonable number of iterations while ensuring that the final margin does not fall outside the range between ML and MH. Of course, it is possible to practice the invention using other formulas or techniques for calculating initial values for ML and MH. [0063] Referring to FIG. 8, a flow chart 210 illustrates operation of software used by the receiver to allocate bits among the different carriers of the multicarrier signal and synchronize changes in the bit allocation table with the transmitter. Processing begins at a first test step 262 which determines if the receiver has received a reference frame. A reference frame is a predetermined and detectable frame of special data bits that is provided by the transmitter to the receiver to allow the receiver to determine the channel characteristics. In a preferred embodiment, the reference frame is transmitted periodically, although other conventional techniques can be used to determine whether the reference frame should be sent by the transmitter. The reference frame is recognized by the receiver using any one of a variety of conventional techniques such as a special header in a packet indicating that a reference frame is being provided. Use of a reference frame in connection with multicarrier,communication is well-known in the art. If a reference frame is not received at the step 262, the software loops back to the test step 262 to poll for receipt of the reference frame. [0064] If it is determined at the test step 262 that a reference frame has been received, then control transfers from the step 262 to a step 264 where the errors in the reference frame are measured with respect to the brown constellation distances of the first signal. Note that since the reference frame is a predetermined signal, the receiver can know exactly what was sent by the transmitter. Therefore, any differences between the data received by the receiver and the expected values for signal data can be accounted for by errors induced by the transmission channel. These errors are measured at the step 264. [0065] Following the step 264 is a step 266 where the receiver determines the channel characteristics based on the errors measured at the step 264. This is done in a conventional manner using techniques for determining channel characteristics based on detected transmission errors. Following the step 266 is a step 268 where the receiver allocates various bits among the carriers using, in a preferred embodiment, the technique disclosed above in connection with FIGS. 6 and 7. [0066] Following the step 268 is a test step 270 which determines if the bit allocation table provided at the step 268 is different than the previous bit allocation table. That is, it is determined at the step 270 if there is a difference between the recently-calculated bit allocation table and the previous bit allocation table. If it is determined at the test step 270 that there is no difference (i.e., that the bit allocation table has not changed), then control transfers from the step 270 back to the step 262 where the software waits for the transmitter to send another reference frame. Otherwise, if it is determined at the step 270 that the new bit allocation table is different than the old bit allocation table, then control transfers from the step 270 to a step 272 where a flag is sent from the receiver to the transmitter indicating that the bit allocation table has changed. In a preferred embodiment, the flag is sent at the step 272 via a single carrier of the multicarrier signal that is reserved for use by the transmitter and receiver only for the flag. In another embodiment, the reserved carrier can also be used to transmit the new bit allocation table. [0067] Following the step 272 is a step 274 where the receiver sends the new bit allocation table, determined at the step 268, to the transmitter. Following the step 274, control transfers back to the test step 262 to poll and wait for the transmitter to send another reference frame. [0068] While the invention has been disclosed in connection with the preferred embodiments shown and described in detail, various modifications and improvements thereon will become readily apparent tot hose skilled in the art. Accordingly, the spirit and scope of the present invention is to be limited only by the following claims. Patent CitationsCited PatentFiling datePublication dateApplicantTitleUS3573380 *May 15, 1969Apr 6, 1971Bell Telephone Labor IncSingle-sideband modulation systemUS4131766 *Jul 11, 1977Dec 26, 1978Granger AssociatesDigital filter bankUS4568156 *Nov 7, 1984Feb 4, 1986Dane John ATracking apparatus for parabolic reflectorsUS4679227 *May 20, 1985Jul 7, 1987Telebit CorporationEnsemble modem structure for imperfect transmission mediaUS4731816 *Jan 12, 1987Mar 15, 1988Telebit CorporationEnsemble modem structure for imperfect transmission mediaUS4802190 *Jun 15, 1987Jan 31, 1989U.S. Philips CorporationMethod of transmitting information by means of code signals, information transmission system for carrying out the method, and transmitting and receiving apparatus for use in the transmission systemUS4912763 *Sep 24, 1987Mar 27, 1990International Business Machines CorporationProcess for multirate encoding signals and device for implementing said processUS5048054 *May 12, 1989Sep 10, 1991Codex CorporationLine probing modemUS5128964 *Oct 10, 1990Jul 7, 1992Intelligent Modem CorporationModulation method and apparatus for multicarrier data transmissionUS5206886 *Apr 16, 1990Apr 27, 1993Telebit CorporationMethod and apparatus for correcting for clock and carrier frequency offset, and phase jitter in mulicarrier modemsUS5285474 *Jun 12, 1992Feb 8, 1994The Board Of Trustees Of The Leland Stanford, Junior UniversityMethod for equalizing a multicarrier signal in a multicarrier communication systemUS5327574 *Feb 20, 1991Jul 5, 1994Mitsubishi Denki Kabushiki KaishaMobile communication systemUS5400322 *Aug 20, 1993Mar 21, 1995Amati Communications Corp.Updating of bit allocations in a multicarrier modulation transmission systemUS5428790 *Oct 8, 1993Jun 27, 1995Fujitsu Personal Systems, Inc.Computer power management systemUS5452288 *Apr 6, 1993Sep 19, 1995France TelecomMethod for the transmission of digital data in radio paging systems and corresponding radio paging receiverUS5479447 *May 3, 1993Dec 26, 1995The Board Of Trustees Of The Leland Stanford, Junior UniversityMethod and apparatus for adaptive, variable bandwidth, high-speed data transmission of a multicarrier signal over digital subscriber linesUS5495483 *Jan 26, 1995Feb 27, 1996Motorola, Inc.Method and apparatus for allocating carrier channelsUS5497398 *Aug 12, 1993Mar 5, 1996Aware, Inc.Multi-carrier transceiverUS5521906 *Jan 26, 1995May 28, 1996Motorola Inc.Method and apparatus for updating carrier channel allocationsUS5533006 *Feb 14, 1994Jul 2, 1996Fujitsu LimitedControl system for a ring type network systemUS5555244 *Jun 30, 1994Sep 10, 1996Integrated Network CorporationScalable multimedia networkUS5596604 *Aug 17, 1993Jan 21, 1997Amati Communications CorporationMulticarrier modulation transmission system with variable delayUS5598435 *Feb 4, 1994Jan 28, 1997British Telecommunications Public Limited CompanyDigital modulation using QAM with multiple signal point constellations not equal to a power of twoUS5636246 *Nov 16, 1994Jun 3, 1997Aware, Inc.Multicarrier transmission systemUS5812599 *Jul 10, 1996Sep 22, 1998Alcatel N.V.Method for allocating data elements in multicarrier applications and equipment to perform this methodUS5822372 *Aug 2, 1996Oct 13, 1998Motorola, Inc.Multicarrier system using subchannel characteristics to implement different error rates within a data streamUS5903608 *Jul 24, 1997May 11, 1999Samsung Electronics Co., Ltd.Adaptive bit swapping method and device for discrete multitone systemUS6052411 *Apr 6, 1998Apr 18, 20003Com CorporationIdle mode for digital subscriber lineUS6072779 *Jun 12, 1997Jun 6, 2000Aware, Inc.Adaptive allocation for variable bandwidth multicarrier communicationUS6266248 *Nov 9, 1999Jul 24, 2001Lucent Technologies Inc.Lockable latch and switch actuator assembly for a circuit cardUS6266348 *Oct 9, 1998Jul 24, 2001Aware, Inc.Splitterless multicarrier modemUS6567473 *Mar 10, 2000May 20, 2003Aware, Inc.Method for seamlessly changing power modes in a ADSL system* Cited by examinerReferenced byCiting PatentFiling datePublication dateApplicantTitleUS7466749 *May 12, 2005Dec 16, 2008Qualcomm IncorporatedRate selection with margin sharingUS7688903 *Dec 5, 2005Mar 30, 2010Nec CorporationMulticarrier transmission apparatus and methodUS8134976Oct 23, 2003Mar 13, 2012Qualcomm IncorporatedChannel calibration for a time division duplexed communication systemUS8145179Oct 31, 2007Mar 27, 2012Qualcomm IncorporatedData detection and demodulation for wireless communication systemsUS8169944Oct 23, 2003May 1, 2012Qualcomm IncorporatedRandom access for wireless multiple-access communication systemsUS8170513Oct 23, 2003May 1, 2012Qualcomm IncorporatedData detection and demodulation for wireless communication systemsUS8194770Aug 27, 2002Jun 5, 2012Qualcomm IncorporatedCoded MIMO systems with selective channel inversion applied per eigenmodeUS8203978Nov 29, 2007Jun 19, 2012Qualcomm IncorporatedMulti-mode terminal in a wireless MIMO systemUS8208364Oct 23, 2003Jun 26, 2012Qualcomm IncorporatedMIMO system with multiple spatial multiplexing modesUS8218609May 31, 2003Jul 10, 2012Qualcomm IncorporatedClosed-loop rate control for a multi-channel communication systemUS8320301Oct 23, 2003Nov 27, 2012Qualcomm IncorporatedMIMO WLAN systemUS8355313May 5, 2008Jan 15, 2013Qualcomm IncorporatedMIMO system with multiple spatial multiplexing modesUS8358714Jul 25, 2005Jan 22, 2013Qualcomm IncorporatedCoding and modulation for multiple data streams in a communication systemUS8462643Jul 15, 2008Jun 11, 2013Qualcomm IncorporatedMIMO WLAN systemUS8483188May 5, 2008Jul 9, 2013Qualcomm IncorporatedMIMO system with multiple spatial multiplexing modesUS8570988Jan 27, 2005Oct 29, 2013Qualcomm IncorporatedChannel calibration for a time division duplexed communication systemUS8711763Jan 19, 2012Apr 29, 2014Qualcomm IncorporatedRandom access for wireless multiple-access communication systemsUS8750151Mar 13, 2012Jun 10, 2014Qualcomm IncorporatedChannel calibration for a time division duplexed communication systemUS8817818 *Apr 21, 2009Aug 26, 2014Texas Instruments IncorporatedBackward compatible bandwidth extensionUS8855226Nov 13, 2008Oct 7, 2014Qualcomm IncorporatedRate selection with margin sharingUS8873365Jun 24, 2009Oct 28, 2014Qualcomm IncorporatedTransmit diversity processing for a multi-antenna communication systemUS8913529Apr 30, 2008Dec 16, 2014Qualcomm IncorporatedMIMO WLAN systemUS8934329Oct 13, 2005Jan 13, 2015Qualcomm IncorporatedTransmit diversity processing for a multi-antenna communication systemUS9013974Aug 13, 2014Apr 21, 2015Qualcomm IncorporatedMIMO WLAN systemUS9031097Dec 29, 2009May 12, 2015Qualcomm IncorporatedMIMO system with multiple spatial multiplexing modesUS9048892Apr 4, 2013Jun 2, 2015Qualcomm IncorporatedMIMO system with multiple spatial multiplexing modesUS9154274Jun 18, 2013Oct 6, 2015Qualcomm IncorporatedOFDM communication system with multiple OFDM symbol sizesUS9240871Apr 30, 2008Jan 19, 2016Qualcomm IncorporatedMIMO WLAN systemUS9312935Jun 8, 2011Apr 12, 2016Qualcomm IncorporatedPilots for MIMO communication systemsUS9473269Dec 1, 2003Oct 18, 2016Qualcomm IncorporatedMethod and apparatus for providing an efficient control channel structure in a wireless communication systemUS20030043901 *Aug 26, 2002Mar 6, 2003Hidenao SatoTone ordering circuit and tone ordering method for an xDSLUS20060120445 *Dec 5, 2005Jun 8, 2006Nec CorporationMulticarrier transmission apparatus and methodUS20060256848 *May 12, 2005Nov 16, 2006Irina MedvedevRate selection wtih margin sharingUS20090268831 *Apr 21, 2009Oct 29, 2009Texas Instruments IncorporatedBackward compatible bandwidth extension* Cited by examinerClassifications U.S. Classification370/468International ClassificationH04L27/26, H04J3/22Cooperative ClassificationH04W72/04, H04L27/2608European ClassificationH04L27/26M1PLegal EventsDateCodeEventDescriptionFeb 16, 2009ASAssignmentOwner name: DAPHIMO CO. 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