Source: https://patents.google.com/patent/WO2012061784A2/en
Timestamp: 2019-11-21 06:58:12
Document Index: 255610223

Matched Legal Cases: ['§ 119', '§ 1', 'Application No. 61', '§ 120', '§ 1', 'Application No. 13', 'Application No. 12', 'Application No. 13217174', 'Application No. 13', 'Application No. 1', 'Application No. 1', 'Application No. 12', 'Application No. 12']

WO2012061784A2 - Switching power converter input voltage approximate zero crossing determination - Google Patents
Switching power converter input voltage approximate zero crossing determination Download PDF
WO2012061784A2
WO2012061784A2 PCT/US2011/059462 US2011059462W WO2012061784A2 WO 2012061784 A2 WO2012061784 A2 WO 2012061784A2 US 2011059462 W US2011059462 W US 2011059462W WO 2012061784 A2 WO2012061784 A2 WO 2012061784A2
PCT/US2011/059462
WO2012061784A3 (en
2011-11-04 Application filed by Cirrus Logic, Inc. filed Critical Cirrus Logic, Inc.
2011-11-04 Priority to US13/290,032 priority
2012-05-10 Publication of WO2012061784A2 publication Critical patent/WO2012061784A2/en
2012-07-05 Publication of WO2012061784A3 publication Critical patent/WO2012061784A3/en
In at least one embodiment, the controller senses a leading edge, phase cut AC input voltage value to a switching power converter during a cycle of the AC input voltage. The controller senses the voltage value at a time prior to a zero crossing of the AC input voltage and utilizes the voltage value to determine the approximate zero crossing. In at least one embodiment, by determining an approximate zero crossing of the AC input voltage, the controller is unaffected by any disturbances of the dimmer that could otherwise make detecting the zero crossing problematic. The particular way of determining an approximate zero crossing is a matter of design choice. In at least one embodiment, the controller approximates the AC input voltage using a function that estimates a waveform of the AC input voltage and determines the approximate zero crossing of the AC input voltage from the approximation of the AC input voltage.
SWITCHING POWER CONVERTER INPUT VOLTAGE APPROXIMATE
ZERO CROSSING DETERMINATION
[001] This application claims the benefit under 35 U.S.C. § 119(e) and 37 C.F.R. § 1.78 of U.S. Provisional Application No. 61/410,269, filed on Nov. 4, 2010, and is incorporated by reference in its entirety. This application also claims the benefit under 35 U.S.C. § 120 and
37 C.F.R. § 1.78 ofU.S. ofU.S. Patent Application No. 13/290,032, filed November 4, 2011, which is incorporated by reference in its entirety
[002] The present invention relates in general to the field of electronics, and more specifically to a method and system for utilizing a switching power converter and determining an
approximate zero crossing of an input voltage to the switching power converter.
[003] Many electronic systems include circuits, such as switching power converters that interface with a dimmer. The interfacing circuits deliver power to a load in accordance with the dimming level set by the dimmer. For example, in a lighting system, dimmers provide an input signal to a lighting system. The input signal represents a dimming level that causes the lighting system to adjust power delivered to a lamp, and, thus, depending on the dimming level, increase or decrease the brightness of the lamp. Many different types of dimmers exist. In general, dimmers generate a digital or analog coded dimming signal that indicates a desired dimming level. For example, some analog based dimmers utilize a triode for alternating current ("triac") device to modulate a phase angle of each cycle of an alternating current ("AC") supply voltage. "Modulating the phase angle" of the supply voltage is also commonly referred to as "phase cutting" the supply voltage. Phase cutting the supply voltage reduces the average power supplied to a load, such as a lighting system, and thereby controls the energy provided to the load.
[004] Once a triac-based dimmer begins conducting during a cycle of an alternating current ("AC") supply voltage, to prevent the triac from disadvantageously, prematurely disconnecting during mid-cycle of the supply voltage, the switching power converter draws a minimum current referred to as a "hold current". As long as an input current to the switching power converter is greater than or equal to the hold current, the triac-based dimmer should not prematurely disconnect. For a leading edge dimmer, a premature disconnect occurs when the dimmer begins conducting and stops conducting prior to reaching a zero crossing of the supply voltage.
Premature disconnects can cause problems with the lighting system, such as flicker and instability.
[005] Figure 1 depicts a lighting system 100 that includes a leading edge, phase-cut dimmer 102. Figure 2 depicts ideal, exemplary voltage graphs 200 associated with the lighting system 100. Referring to Figures 1 and 2, the lighting system 100 receives an AC supply voltage VIN from voltage supply 104. The supply voltage VIN, indicated by voltage waveform 202, is, for example, a nominally 60 Hz/110 V line voltage in the United States of America or a nominally 50 Hz/220 V line voltage in Europe. A leading edge dimmer 102 phase cuts leading edges, such as leading edges 204 and 206, of each half cycle of supply voltage VIN- Since each half cycle of supply voltage VIN is 180 degrees of the supply voltage VIN, the leading edge dimmer 102 phase cuts the supply voltage ViN at an angle greater than 0 degrees and less than 180 degrees.
Generally, the voltage phase cutting range of a leading edge dimmer 102 is 10 degrees to 170 degrees.
[006] The input signal voltage Vo jN to the lighting system 100 represents a dimming level that causes the lighting system 100 to adjust power delivered to a lamp 122, and, thus, depending on the dimming level, increase or decrease the brightness of the lamp 122. The leading edge dimmer 102 can be any type of leading edge dimmer, such as a triac-based leading edge dimmer available from Lutron Electronics, Inc. of Coopersberg, PA ("Lutron"). A triac-based leading edge dimmer is described in the Background section of U.S. Patent Application No. 12/858,164, entitled Dimmer Output Emulation, filed on August 17, 2010, and inventor John L. Melanson. [007] The phase cut dimmer 102 supplies the input voltage Vo IN as modified by the phase cut dimmer 102 to a full bridge diode rectifier 106. The full bridge rectifier 106 supplies an AC rectified voltage VORJN to the switching power converter 108. Thus, since the input voltage Vo IN is derived from the input supply voltage VIN, the rectified input voltage VOR JN is also derived from the input supply voltage VIN- Capacitor 110 filters high frequency components from rectified voltage VOR JN. TO control the operation of switching power converter 108, controller 110 generates a control signal CSo to control conductivity of field effect transistor (FET) switch 112. The control signal CSo is a pulse width modulated signal. Control signal CSo waveform 114 represents an exemplary control signal CSo. Each pulse of control signal CSo turns switch 112 ON (i.e. conducts), and the inductor current iL increases, as shown in the exemplary inductor current waveform 115, to charge inductor 116 during a charging phase Tc. Diode 118 prevents current flow from link capacitor 120 into switch 112. When the pulse ends, the inductor 116 reverses voltage polarity (commonly referred to as "flyback"), and the inductor current iL decreases during the flyback phase TFB, as shown in inductor current waveform 115. The inductor current 1L boosts the link voltage across the link capacitor 120 through diode 118.
[008] The switching power converter 108 is a boost-type converter, and, thus, the link voltage VLINK is greater than the rectified input voltage VOR jN. Controller 110 senses the rectified input voltage VOR IN at node 124 and senses the link voltage VLINK at node 126. Controller 110 operates the switching power converter 108 to maintain an approximately constant link voltage VLINK for lamp 122, provide power factor correction, and correlate the output current ί0υτ with the phase cut angle of the rectified input voltage VOR IN. Lamp 132 includes one or more light emitting diodes.
[009] It is desirable to improve interfacing with triac-based dimmers. SUMMARY OF THE INVENTION
[0010] In one embodiment of the present invention, an apparatus includes a controller having an input to sense a leading edge, phase cut alternating current (AC) input voltage to a switching power converter at least at a first time during a cycle of the AC input voltage. The cycle of the AC input voltage is derived from a cycle of the AC input supply voltage, and the first time is prior to an approximate zero crossing of the cycle of the AC input supply voltage. At least some zero crossings of the AC input supply voltage are not directly observable by the controller. The controller is configured to determine the approximate zero crossing of the AC input supply voltage based on a voltage value of the phase cut AC input voltage sensed at the first time.
[0011] In another embodiment of the present invention, a method includes receiving a sense signal indicating a leading edge, phase cut alternating current (AC) input voltage to a switching power converter. The sense signal is received at least at a first time during a cycle of the AC input voltage, the cycle of the AC input voltage is derived from a cycle of the AC input supply voltage, and the first time is prior to an approximate zero crossing of the cycle of the AC input supply voltage. At least some zero crossings of the AC input supply voltage are not directly observable by a controller of a switching power converter. The method further includes determining the approximate zero crossing of the AC input supply voltage based on a voltage value of the phase cut AC input voltage sensed at the first time.
[0012] In another embodiment of the present invention, a method includes exposing a leading edge, phase cut alternating current (AC) input voltage supplied to a switching power converter for part of a cycle of the AC input voltage. The exposed AC input voltage is used to supply current to a load, and the AC input voltage is derived from an AC input supply voltage. The method further includes sensing the AC input voltage and ceasing exposure of the AC input voltage after sensing the AC input voltage. The method further includes determining an approximate zero crossing of the AC input supply voltage based on a value of the sensed AC input voltage.
[0013] In a further embodiment of the present invention, an apparatus includes means for receiving a sense signal indicating a leading edge, phase cut alternating current (AC) input voltage to a switching power converter. The sense signal is received at least at a first time during a cycle of the AC input voltage, the cycle of the AC input voltage is derived from a cycle of the AC input supply voltage, and the first time is prior to an approximate zero crossing of the cycle of the AC input supply voltage. At least some zero crossings of the AC input supply voltage are not directly observable by a controller of a switching power converter. The apparatus further includes means for determining the approximate zero crossing of the AC input supply voltage based on a voltage value of the phase cut AC input voltage sensed at the first time. BRIEF DESCRIPTION OF THE DRAWINGS
[0015] Figure 1 (labeled prior art) depicts a lighting system that includes a triac-based dimmer.
[0016] Figure 2 (labeled prior art) depicts exemplary voltage graphs associated with the lighting system of Figure 1.
[0017] Figure 3 depicts an electronic system that includes a controller having a zero crossing calculator.
[0018] Figure 4 depicts exemplary input supply voltage and a rectified input voltage for the system of Figure 3.
[0019] Figure 5 depicts a controller that represents an embodiment of the controller of Figure 3.
[0020] Figure 6 depicts an exemplary approximate zero crossing determination process.
[0021] Figure 7 depicts exemplary approximate zero crossing determination code.
[0022] Figure 8 depicts an exemplary capacitor/current model utilized by the approximate zero crossing determination code of Figure 7.
[0023] Figure 9 depicts an electronic system that represents an embodiment of the electronic system of Figure 3.
[0024] In at least one embodiment, an electronic system includes a controller, and the controller determines an approximate zero crossing of an alternating current (AC) input supply voltage to a switching power converter based on a voltage value of the AC input voltage. The term
"approximate" as used herein means exact or sufficiently exact. A zero crossing is sufficiently exact if the zero crossing can be used by the controller in lieu of the actual zero crossing.
Actually 'detecting' a zero crossing of the AC input supply voltage, as opposed to 'determining' an approximate zero crossing of the AC input supply voltage, can be problematic in some circumstances. For example, triac-based dimmers have conventionally been used with incandescent lamps. Incandescent lamps are generally immune from disturbances in the phase cut voltage from the triac-based dimmer, such as premature disconnection and electronic noise generated by a triac-based dimmer. However, disturbances of a supply voltage by a dimmer, such as premature disconnection, premature conduction, and electronic noise, can be problematic to relatively low-power, actively controlled electronic systems, such as light emitting diode (LED) based lighting systems. In at least one embodiment, the controller utilizes the zero crossing of the AC input voltage to begin one or more operations, such as providing a sufficiently low input impedance for the dimmer at the zero crossing to hold a dimmer output voltage at approximately zero volts as described in, for example, U.S. Patent Application. No. 12/858,164, filed August 17, 2010, entitled: "Dimmer Output Emulation", and inventor: John L. Melanson (referred to herein as "Melanson I") and U.S. Patent Application No. 13217174, filed August 24, 2011, entitled: "Multi-Mode Dimmer Interfacing Including Attach State Control", and inventors: Eric J. King and John L. Melanson, which are both incorporated by reference in their entireties.
[0025] In at least one embodiment, the controller senses a leading edge, phase cut AC input voltage value to a switching power converter during a cycle of the AC input voltage. The controller senses the voltage value at a time prior to a zero crossing of the AC input voltage. The controller utilizes the voltage value to determine an approximate zero crossing of the AC input supply voltage. In at least one embodiment, by determining an approximate zero crossing of the AC input voltage, the controller is unaffected by any disturbances of the dimmer that could otherwise make detecting the zero crossing from sensing the actual AC input voltage
problematic. The particular way of determining an approximate zero crossing is a matter of design choice. In at least one embodiment, the controller approximates the AC input voltage using a function that estimates a waveform of the AC input voltage and determines the approximate zero crossing of the AC input voltage from the approximation of the AC input voltage. The particular function can be any type of function, such as a polynomial function or a trigonometric function. In at least one embodiment, the controller includes dedicated circuits to determine the approximate zero crossing. In at least one embodiment, the controller includes a processor and a memory, and the memory includes code that is executable by the processor to determine the approximate zero crossing. In at least one embodiment, the controller includes a look-up table that identifies when the zero crossing will occur based on the sensed voltage value.
[0026] Determining when to sense the voltage value during a cycle of the AC input voltage is a matter of design choice. In at least one embodiment, the controller senses the voltage value during a portion of the AC input voltage when the dimmer has a high probability of providing a relatively undisturbed input voltage to the switching power converter. Sensing the voltage value during a relatively undisturbed portion of the AC input voltage allows the controller to utilize a voltage value that accurately represents a voltage value of a supply voltage to the dimmer.
Additionally, in at least one embodiment, the controller senses the voltage value when the phase cut voltage is relatively undisturbed and when the switching power converter has received sufficient power to meet power demands by a load. In at least one embodiment, after the controller senses the voltage value, the controller causes the electronic system to dissipate excess energy as, for example, (i) described in U.S. Patent Applications 13/289,845, filed November 4, 201 1 , entitled "Controlled Power Dissipation in a Switch Path in a Lighting System", and inventors John L. Melanson and Eric J. King, (ii) U.S. Patent Application No. 13/289,93 1 , filed November 4, 201 1 , entitled "Controlled Power Dissipation in a Lighting System", and inventors John L. Melanson and Eric J. King, (iii) 13/289,967 filed November 4, 201 1 , entitled "Controlled Power Dissipation in a Link Path in a Lighting System", and inventors John L. Melanson and Eric J. King, and/or (iv) dissipate power through another power dissipation circuit. The U.S. Patent Applications identified in (i), (ii), and (iii) are collectively referred to as the "Power Dissipation Applications".
[0027] Figure 3 depicts an electronic system 300 that includes a zero crossing calculator 302 of controller 304 that determines the approximate zero crossing of the rectified input voltage
OR IN- Figure 4 depicts exemplary voltage waveforms 400 of the input supply voltage ViN and rectified input voltage VOR IN- Referring to Figures 3 and 4, dimmer 306 is a leading edge, phase cut dimmer. Dimmer 306 can be any type of leading edge, phase cut dimmer including a triac- based dimmer or a field effect transistor (FET) based dimmer. One cycle of the input supply voltage VIN is depicted in Figure 4. The rectified input voltage VOR IN depicts two cycles, cycle A and cycle B, which are derived from the cycle 401 of the input supply voltage VIN- Cycle A is a phase cut version of the first half cycle 402 of the input supply voltage VIN, and cycle B is a rectified, phase cut version of the second half cycle 404 of the input supply voltage ViN. Cycle A occurs from time t0 until the zero crossing of the input supply voltage VIN at time t3. Cycle B occurs from time t3 until the next zero crossing at time t6 of the input supply voltage VIN- In at least one embodiment, the dimmer 306 phase cuts the input supply voltage VIN from voltage supply 104 to generate the phase cut input voltage Vo IN. The full-bridge diode rectifier rectifies the phase cut input voltage Vo IN to generate the rectified input voltage VOR IN. Between times t0 and tls the dimmer 306 does not conduct current from the voltage supply 104 and, thus, phase cuts the supply voltage VIN until time t . At time tls the dimmer 306 conducts so that the rectified input voltage VO JN equals the input voltage VIN- At time t2, the controller 304 senses the voltage value V(0)A of rectified input voltage VO JN during cycle A of the rectified input voltage VOR IN- The place and manner of sensing a voltage value of the rectified input voltage VOR IN that represents a voltage value of the input supply voltage ViN is a matter of design choice. In at least one embodiment, the controller 304 senses the voltage value V(0)A
downstream (right side) of the rectifier 106 from the phase-cut input voltage Vo IN. In at least one embodiment, the controller 304 senses the voltage value V(0)A upstream (left side) of the rectifier 106 from the phase-cut input voltage Vo IN.
[0028] The controller 304 includes a zero crossing calculator 302 to determine an approximate zero crossing of the rectified input voltage VOR IN. For cycle A of the rectified input voltage VOR IN, the zero crossing occurs at time t3. The particular implementation of the zero crossing calculator 302 is a matter of design choice. Various exemplary embodiments of the zero crossing calculator 302 are subsequently described in more detail. In at least one embodiment, the time t2 is selected as the time to sense the voltage value V(0)A because the power converter 308 has received sufficient power from voltage supply 104 to maintain an approximately constant link voltage VLINK and meet power demands of load 310. In at least one embodiment, at time t2 the controller 304 maintains the rectified input voltage VOR IN at the voltage value V(0)A until reaching the zero crossing at time t3. Maintaining the voltage of the rectified input voltage VOR IN effectively stops the current flow iiN into the power converter 308. At the zero crossing, in at least one embodiment, the controller 304 causes the rectified input voltage VORJN to rapidly decrease to approximately 0 volts. How to dissipate the energy associated with decreasing the rectified input voltage VOR IN to approximately 0 volts is also a matter of design choice. In at least one embodiment, the power is dissipated as, for example, described in any or all of the Power Dissipation Applications and/or through another power dissipation circuit.
[0029] Controller 304 continues to determine the approximate zero crossing of the rectified input voltage VOR IN in subsequent cycles of the rectified input voltage VOR jN as, for example, shown in cycle B. In cycle B of the rectified input voltage VOR IN, the phase cut dimmer 306 phase cuts the rectified input voltage VOR IN from time t3 until time t4. At time t5, the controller 304 senses the voltage value V(0)B of the rectified input voltage VORJN at time t5. The zero crossing calculator 302 then determines the approximate zero crossing time that occurs at time t6 as previously described. In at least one embodiment, the actual zero crossings of the rectified input voltage VOR IN are not directly observable by the controller 304, and, thus, are not actually detectable by the controller 304. In at least one embodiment, for a 120 Hz rectified input voltage OR IN, the sensing times of the rectified input voltage VOR jN, such as times t2 and t5, are within a range 0.5-5 ms of the approximate zero crossing time, such as respective times t3 and t6. The sensing times of the rectified input voltage VOR IN, such as times t2 and t5, are within a range of 0.25-5 ms of the approximate zero crossing time, such as respective times t3 and t6. In at least one embodiment, the range sensing times are inversely linearly related with respect to the frequency of the rectified input voltage VOR IN, e.g. for a 240 Hz rectified input voltage VOR IN, the sensing times are reduced by 50%. In at least one embodiment, the sensed voltage, such as sensed voltage V(0)A and V(0)B, are greater than or equal to 50V or, in at least one embodiment, greater than 0.3 times an RMS peak value of the rectified input voltage VOR IN.
[0030] The controller 304 controls the power converter 308. The particular type of power converter 308 is a matter of design choice. For example, the power converter 308 can be a boost-type switching power converter such as switching power converter 108, a buck type switching power converter, a boost-buck type switching power converter, or a Ciik type switching power converter. In at least one embodiment, controller 304 controls the power converter 308 as described in, for example, U.S. Patent Application No. 1 1/967,269, entitled "Power Control System Using a Nonlinear Delta-Sigma Modulator With Nonlinear Power Conversion Process Modeling", filed on December 3 1 , 2007, inventor John L. Melanson
(referred to herein as "Melanson Π"), U.S. Patent Application No. 1 1/967,275, entitled
"Programmable Power Control System", filed on December 31 , 2007, and inventor John L. Melanson (referred to herein as "Melanson III"), U.S. Patent Application No. 12/495, 457, entitled "Cascode Configured Switching Using at Least One Low Breakdown Voltage Internal, Integrated Circuit Switch to Control At Least One High Breakdown Voltage External Switch", filed on June 30, 2009 ("referred to herein as "Melanson IV"), and inventor John L. Melanson, and U.S. Patent Application No. 12,174,404, entitled "Constant Current Controller With Selectable Gain", filing date June 30, 2011, and inventors John L. Melanson, Rahul Singh, and Siddharth Maru (referred to herein as "Melanson V"),, which are all incorporated by reference in their entireties.
[0031] Figure 5 depicts a controller 500, which represents one embodiment of controller 304. Controller 500 includes zero crossing calculator 502, which represents one embodiment of the zero crossing calculator 302. Figure 6 depicts an approximate zero crossing determination process 600, which represents one embodiment of an approximate zero crossing determination process utilized by the controller 500 to determine an approximate zero crossing of the rectified input voltage VOR IN.
[0032] Referring to Figures 5 and 6, in operation 602, the controller 500 observes the rectified input voltage VOR IN. In operation 604, the controller selects a value v(0) of the rectified input voltage VOR IN and stores the selected value v(0) in a register 504. The zero crossing calculator 500 includes a memory 506 that stores approximate zero crossing determination code 508. The processor 510 communicates with the memory 506 and, in operation 606, executes the approximate zero crossing determination code 508 to synthesize the rectified input voltage VOR IN and determine an approximate zero crossing of the synthesized rectified input voltage VOR IN- The processor 510 utilizes the sensed voltage value V(0) as an initial value to determine an approximate zero crossing of the rectified input voltage VOR IN. The particular
implementation of the approximate zero crossing determination code 508 is a matter of design choice. In at least one embodiment, the approximate zero crossing determination code 508 implements a parabolic function as, for example, subsequently describedError! Reference source not found.. In other embodiments, the approximate zero crossing determination code 508 implements other polynomial functions or trigonometric functions, such as an actual sine function, to synthesize the rectified input voltage VORJN to determine zero crossings of the rectified input voltage VOR JN- In at least one embodiment, the approximate zero crossing determination code 508 includes code to access a look up table, and the look up table includes zero crossing times corresponding to possible values of the sensed voltage value V(0).
[0033] Figures 7A and 7B collectively depict zero crossing code 700, which represents one embodiment of the zero crossing code 508. The zero crossing code 700 begins in Figure 7A and continues in Figure 7B. The zero crossing code 700 implements an iterative approximate zero crossing determination process using a parabolic function based on modeling changes in voltage across a capacitor resulting from current flow from the capacitor. Figure 8 depicts an exemplary capacitor/current model 800 utilized by the zero crossing code 700. The capacitor/current model 800 models the input supply voltage ViN using a parabolic function to synthesize the input supply voltage Vm.
[0034] Referring to Figures 7 and 8, the zero crossing code 700 utilizes an initial sample V(0) of the rectified input voltage VOR jN. The capacitor/current model 800 models the sampling with a switch 802 that momentarily closes at a time tsENSE and then immediately opens. The time tsENSE at which the rectified input voltage VO JN is sensed is a matter of design choice and, in at least one embodiment, is selected on a cycle-by-cycle basis of the rectified input voltage VOR IN. In at least one embodiment, the sensing time t0 occurs when the voltage supply 104 (Figure 3) has supplied sufficient power to meet the power demand of load 310 (Figure 3). Thus, in at least one embodiment, the time tsENSE corresponds to time t2 for cycle A and time t5 for cycle B of the rectified input voltage VO JN as depicted in Figure 4. In at least one embodiment, for a 120 Hz rectified input voltage VOR IN, the time tsENSE is within 0.5-5 ms of the zero crossing time tZc- In at least one embodiment, for a 120 Hz rectified input voltage VOR IN, the time tsENSE is within 0.25-5 ms of the zero crossing time tZc-
[0035] The voltage-current graph 804 models a current I(V(n)) as a function of the voltage V(n) across the capacitor 806, i.e. I(V(n)) = f(V(n)). The voltage-current graph 804 presents a linear relationship between the voltage V(n) across the capacitor 806 and the current I(V(n)) as, for example, represented by Equation [1] :
I(V(n))= m-V(n) +b [1]
"V(n)" represents the voltage across capacitor 806, which represents the input supply voltage VIN. "I(V(n))" represents the current discharged from capacitor 806 and is modeled by a varying current source 810. "m" is the slope of the V(n)/I(V(n)) relationship line 808, and "b" is the y- intercept of the V(n)/I(V(n)) relationship line 808. The values of "m" and "b" are a matter of design choice and are, in at least one embodiment, chosen to best approximate an actual relationship between the input supply voltage VIN and the input current iiN (Figure 3) for the modeled capacitor 806.
[0036] The change in voltage V(n) with respect to time is represented by Equation [2]:
dV(n)/dt = I(V)/C [2].
"dV(n)/dt" represents the change in voltage with respect to time, and "C" represents a capacitance of capacitor 806. In at least one embodiment, for ease of calculation, C = 1. "dt" represents a change in time, and, in at least one embodiment, is a constant time period at which the zero crossing indicator value ZC is updated. The particular value of dt is a matter of design choice. In at least one embodiment, the value of dt is chosen based on a desired accuracy of the zero crossing indicator value ZC. In at least one embodiment, the zero crossing value ZC is updated at a frequency fcALC, and fcALC is at least 10 kHz. Thus, dt, which equals 1/fcALC, is less than or equal to 0.0001 sees.
[0037] Equation [2] can be rearranged as Equation [3]:
dV(n) =(I(V)/C)-dt [3].
V(n+l) = V(n) - dV(n) [4].
[0038] The initial value V(0) is provided by an actual sensed value of rectified input voltage VOR IN at time tsENSE- The voltage-current graph 804 provides a value of I(V) for each sample or calculation of V(n), and the value of each dV(n) for each increment of dt can, thus, be determined from Equation [3] and the value of I(V) from the voltage-current graph 804. Since the relationship between V(n) and I(V) is linear in voltage-current graph 804, the combination of Equations [l]-[4] result in a parabolic function, and the values of V(n+1) will decrease in accordance with the parabolic function of Equation [4]. The input supply voltage VIN is, in at least one embodiment, a sine wave. The parabolic function of Equation [4] is relatively fast and easy to calculate and closely models a sine wave. [0039] Comparator 812 compares the voltage value V(n) with a reference value VZc REF, and the zero crossing value ZC represents the result of the comparison. The reference value VZC_REF is chosen so that when the voltage value V(n) is less than the reference value VZC_REF, the zero crossing value ZC changes state from a logical 0 to a logical 1 to indicate a zero crossing of the input supply voltage ViN. In at least one embodiment, when the zero crossing of the input supply voltage VIN has been reached, the controller 304 (Figure 3) transitions to hold or "glue" the rectified input voltage VOR IN at a low value to prevent the phase cut dimmer 306 from prematurely firing during the next cycle of the input supply voltage ViN as, for example, described in Melanson I.
[0040] Equation [5] represents an approximation equation that can be used to iteratively determine an approximate zero crossing of the AC input supply voltage VIN:
VAppRox(i) = VAppRox(i-l)-[kr VAppRox[i-l] k2 [5].
"VAPpRox(i)" is the z'th approximate zero crossing of the AC input supply voltage VIN, "i" is an integer index, "VAPpRox(i-l)" is the approximate zero crossing value that immediately precedes the value of VAPPROX(I)- "ki" and "k2" are scaling factors, ki relates to the peak value of the input supply voltage and k2 relates to the frequency and, thus, the step-size of each iteration of Equation [5].
[0041 ] For a 120 Vrms, 60 Hz input supply voltage,
= 220, k2 = 0.38, and starting at a 1 12 degree phase cut, the values of VAPPROX(I) rounded to the nearest volt for Equation [5] are:
{ 157, 155, 152, 150, 147, 145, 142, 139, 136, 132, 129, 126, 122, 1 18, 1 14, 1 10, 106, 102, 97, 93, 88, 83, 78, 72, 67, 61 , 55, 49, 42, 35, 28, 21 , 13, 5, 0}
The actual sine wave values are:
{ 157, 155, 153, 150, 147, 144, 141 , 137, 134, 130, 126, 122, 1 18, 1 14, 109, 104, 100, 95, 90, 85, 80, 74, 69, 64, 58, 52, 47, 41 , 35, 29, 24, 18, 12, 6, 0}
For a 120 Vrms, 60 Hz input supply voltage,
= 220, k2 = 0.38, and starting at a 130 degree phase cut, the values of VAPPROX(I) rounded to the nearest volt for Equation [5] are:
{ 130, 127, 123, 1 19, 1 16, 1 12, 107, 103, 99, 94, 89, 84, 79, 74, 68, 63, 57, 50, 44, 37, 30, 23, 16, 8, 0, -9} The actual sine wave values are:
{ 130, 126, 122, 1 18, 1 14, 109, 104, 100, 95, 90, 85, 80, 74, 69, 64, 58, 52, 47, 41 , 35, 29, 24, 18, 12, 6, 0}
[0042] Thus, there is a slight error between the actual zero crossing as indicated by the sine wave data and the determined approximate zero crossing determined using Equation [5] . However, the approximation of the zero crossing is sufficient to allow the controller 506 to accurately control the power converter 308 and maintain compatibility with the phase-cut dimmer 306. More accurate functions can be used if higher accuracy is desired.
[0043] Figure 9 depicts an electronic system 900, which represents one embodiment of the electronic system 300. Controller 902 senses the rectified input voltage VOR JN at node 124. Controller 902 can sense the rectified input voltage VOR jN in any desired manner, such as through a resistor divider circuit 905. Zero crossing calculator 904, which represents one embodiment of the zero crossing calculator 302 (Figure 3), synthesizes the rectified input voltage OR IN as, for example, previously described in conjunction with zero crossing calculator 302, 500 (Figure 5), or 700 (Figure 7). In at least one embodiment, controller 902 controls the switching power converter as, for example, Melanson II, Melanson III, Melanson IV, or
Melanson V.
[0044] Thus, a controller senses a leading edge, phase cut alternating current (AC) input voltage to a switching power converter at least at a time t0 during a cycle of the AC input voltage. The time to is prior to a zero crossing of the AC input voltage and at least some zero crossings of the AC input voltage are not directly observable by the controller. The controller is configured to determine an approximate zero crossing of the AC input voltage based on a voltage value of the AC input voltage at time t0.
[0045] Although embodiments have been described in detail, it should be understood that various changes, substitutions, and alterations can be made hereto without departing from the spirit and scope of the invention as defined by the appended claims.
a controller having an input to sense a leading edge, phase cut alternating current (AC) input voltage to a switching power converter at least at a first time during a cycle of the AC input voltage, wherein the cycle of the AC input voltage is derived from a cycle of the AC input supply voltage, the first time is prior to an approximate zero crossing of the cycle of the AC input supply voltage, and at least some zero crossings of the AC input supply voltage are not directly observable by the controller, and the controller is configured to: determine the approximate zero crossing of the AC input supply voltage based on a voltage value of the phase cut AC input voltage sensed at the first time.
2. The apparatus of claim 1 wherein to determine the approximate zero crossing of the AC input supply voltage, the controller is configured to:
approximate the AC input supply voltage using a function that estimates a waveform of the AC input supply voltage and determine the approximate zero crossing of the AC input supply voltage from the approximation of the AC input supply voltage.
5. The apparatus of claim 1 wherein to determine the approximate zero crossing of the AC input supply voltage, the controller is configured to:
synthesize the AC input supply voltage to determine a delay to the approximate zero crossing from the first time.
7. The apparatus of claim 1 wherein to determine the approximate zero crossing of the AC input supply voltage, the controller is configured to:
observe the phase cut AC input voltage during a cycle of the phase cut AC input voltage for during a first time period beginning at or before the leading edge of the AC input supply voltage until when the phase cut AC input voltage disconnects from a switching power converter; and
utilize data associated with the observation of the phase cut AC input voltage from the first time period to determine the approximate zero crossing of the AC input supply voltage.
9. The apparatus of claim 7 wherein to determine the approximate zero crossing of the AC input supply voltage, the controller is configured to:
iteratively approximate the AC input supply voltage after the first time period until the iterative approximation indicates that the AC input supply voltage equals approximately zero.
10. The apparatus of claim 1 wherein the controller is further configured to:
expose the phase cut AC input voltage to an input voltage node of the controller at the first time while current is drawn through the switching power converter by a load.
12. The apparatus of claim 1 wherein the controller is further configured to:
hold the rectified phase cut AC input voltage at a constant value until the controller
determines the approximate zero crossing of the AC input supply voltage; and release the phase cut AC input voltage at a time of the approximate zero crossing of the AC input supply voltage as determined by the controller.
receiving a sense signal indicating a leading edge, phase cut alternating current (AC) input voltage to a switching power converter, wherein the sense signal is received at least at a first time during a cycle of the AC input voltage, the cycle of the AC input voltage is derived from a cycle of the AC input supply voltage, the first time is prior to an approximate zero crossing of the cycle of the AC input supply voltage, and at least some zero crossings of the AC input supply voltage are not directly observable by a controller of a switching power converter; and determining the approximate zero crossing of the AC input supply voltage based on a voltage value of the phase cut AC input voltage sensed at the first time.
16. The method of claim 15 wherein determining the approximate zero crossing of the AC input supply voltage further comprises:
estimating a waveform of the AC input supply voltage; and
determining the approximate zero crossing of the AC input supply voltage from the
approximation of the AC input supply voltage.
17. The method of claim 16 wherein estimating a waveform of the AC input supply voltage further comprises:
approximating the AC input supply voltage using a function that estimates a waveform of the AC input supply voltage.
20. The method of claim 15 wherein determining the approximate zero crossing of the AC input supply voltage further comprises:
synthesizing the AC input supply voltage to determine a delay to the approximate zero crossing from the first time.
22. The method of claim 15 wherein determining the approximate zero crossing of the AC input supply voltage further comprises:
observing the phase cut AC input voltage during a cycle of the phase cut AC input
voltage for during a first time period beginning at or before the leading edge of the AC input supply voltage until when the phase cut AC input voltage disconnects from a switching power converter; and
utilizing data associated with the observation of the phase cut AC input voltage from the first time period to determine the approximate zero crossing of the AC input supply voltage.
24. The method of claim 22 wherein determining the approximate zero crossing of the AC input supply voltage further comprises:
iteratively approximating the AC input supply voltage after the first time period until the iterative approximation indicates that the AC input supply voltage equals approximately zero.
exposing the phase cut AC input voltage to an input voltage node of the controller at the first time while current is drawn through the switching power converter by a load.
27. The method of claim 15 wherein the controller is further configured to:
28. The method of claim 27 wherein releasing the phase cut AC input voltage at a time of the determined approximate zero crossing of the AC input supply voltage further comprises:
releasing the phase cut AC input voltage when the controller determines the approximate zero crossing of the AC input supply voltage.
exposing a leading edge, phase cut alternating current (AC) input voltage supplied to a switching power converter for part of a cycle of the AC input voltage, wherein the exposed AC input voltage is used to supply current to a load and the AC input voltage is derived from an AC input supply voltage;
sensing the AC input voltage;
ceasing exposure of the AC input voltage after sensing the AC input voltage; and determining an approximate zero crossing of the AC input supply voltage based on a value of the sensed AC input voltage.
means for receiving a sense signal indicating a leading edge, phase cut alternating current (AC) input voltage to a switching power converter, wherein the sense signal is received at least at a first time during a cycle of the AC input voltage, the cycle of the AC input voltage is derived from a cycle of the AC input supply voltage, the first time is prior to an approximate zero crossing of the cycle of the AC input supply voltage, and at least some zero crossings of the AC input supply voltage are not directly observable by a controller of a switching power converter; and means for determining the approximate zero crossing of the AC input supply voltage based on a voltage value of the phase cut AC input voltage sensed at the first time.
PCT/US2011/059462 2010-11-04 2011-11-04 Switching power converter input voltage approximate zero crossing determination WO2012061784A2 (en)
US13/290,032 2011-11-04
CN201180052963.0A CN103270678B (en) 2010-11-04 2011-11-04 Switching power converter input voltage is approximately zero crossing determination
EP11782743.6A EP2636134A2 (en) 2010-11-04 2011-11-04 Switching power converter input voltage approximate zero crossing determination
WO2012061784A2 true WO2012061784A2 (en) 2012-05-10
WO2012061784A3 WO2012061784A3 (en) 2012-07-05
ID=46025149
PCT/US2011/059462 WO2012061784A2 (en) 2010-11-04 2011-11-04 Switching power converter input voltage approximate zero crossing determination
US (2) US8610365B2 (en)
EP (1) EP2636134A2 (en)
CN (1) CN103270678B (en)
WO (1) WO2012061784A2 (en)
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CN105510690B (en) * 2014-09-22 2018-04-27 登丰微电子股份有限公司 Zero passage voltage detection circuit and method
CA2727529A1 (en) * 2008-06-13 2009-12-17 Queen's University At Kingston Dimmable single stage electronic ballast with high power factor
CN101505568B (en) * 2009-03-12 2012-10-03 深圳市众明半导体照明有限公司 LED light modulating apparatus suitable for light modulator
2011-11-04 EP EP11782743.6A patent/EP2636134A2/en not_active Withdrawn
2011-11-04 CN CN201180052963.0A patent/CN103270678B/en active IP Right Grant
2011-11-04 WO PCT/US2011/059462 patent/WO2012061784A2/en active Application Filing
2011-11-04 US US13/290,032 patent/US8610365B2/en active Active
2013-12-12 US US14/104,137 patent/US20160056808A9/en not_active Abandoned
CN103270678A (en) 2013-08-28
US20160056808A9 (en) 2016-02-25
EP2636134A2 (en) 2013-09-11
WO2012061784A3 (en) 2012-07-05
US20150171853A1 (en) 2015-06-18
US20120286826A1 (en) 2012-11-15
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