Source: http://www.google.com/patents/US5892468?dq=6011510
Timestamp: 2017-02-26 08:01:05
Document Index: 683571233

Matched Legal Cases: ['art 13', 'art 15', 'art 13', 'art 13', 'art 15', 'art 15', 'art 15', 'art 15', 'art 15', 'art 51', 'art 13', 'art 90', 'art 15', 'art 90', 'art 51', 'art 51', 'art 90', 'art 274', 'art 276', 'art 276', 'art 303', 'arts 13', 'arts 13', 'arts 15', 'arts 15']

Patent US5892468 - Digital-to-digital conversion using nonuniform sample rates - Google PatentsSearch Images Maps Play YouTube News Gmail Drive More »Sign inPatentsA method and apparatus for digital-to-digital conversion using sigma-delta modulation of the temporal spacing between digital samples. The method and apparatus of the present invention provides for sigma-delta modulation of the time base such that noise produced by NONUNIFORM sampling are frequency-shaped...http://www.google.com/patents/US5892468?utm_source=gb-gplus-sharePatent US5892468 - Digital-to-digital conversion using nonuniform sample ratesAdvanced Patent SearchTry the new Google Patents, with machine-classified Google Scholar results, and Japanese and South Korean patents.Publication numberUS5892468 APublication typeGrantApplication numberUS 08/732,421PCT numberPCT/US1995/003739Publication dateApr 6, 1999Filing dateMar 23, 1995Priority dateSep 13, 1993Fee statusPaidPublication number08732421, 732421, PCT/1995/3739, PCT/US/1995/003739, PCT/US/1995/03739, PCT/US/95/003739, PCT/US/95/03739, PCT/US1995/003739, PCT/US1995/03739, PCT/US1995003739, PCT/US199503739, PCT/US95/003739, PCT/US95/03739, PCT/US95003739, PCT/US9503739, US 5892468 A, US 5892468A, US-A-5892468, US5892468 A, US5892468AInventorsJames Wilson, Ronald A. Cellini, James M. SobolOriginal AssigneeAnalog Devices, Inc.Export CitationBiBTeX, EndNote, RefManPatent Citations (22), Non-Patent Citations (16), Referenced by (43), Classifications (19), Legal Events (3) External Links: USPTO, USPTO Assignment, EspacenetDigital-to-digital conversion using nonuniform sample rates
US 5892468 AAbstract
A method and apparatus for digital-to-digital conversion using sigma-delta modulation of the temporal spacing between digital samples. The method and apparatus of the present invention provides for sigma-delta modulation of the time base such that noise produced by NONUNIFORM sampling are frequency-shaped to a region (i.e., shifted to higher frequencies where it can be removed by conventional filtering techniques. In one embodiment, the digital data is interpolated (16) by fixed ratio and then decimated (21) under control of a first sigma-delta modulated frequency selection signal (26) that represents, on average, the data rate of the incoming digital data stream. Thereafter, the digital data is interpolated (30) under control of a second sigma-delta modulated frequency selection signal (46) that represents, on average, the data rate of the digital data to be output by the converter and then decimated (40) by a fixed ratio. In another embodiment, the digital data is interpolated under control of a first sigma-delta modulated frequency selection signal that represents, on average, the data rate of the incoming digital data stream and then decimated by a fixed ratio. Thereafter, the digital data is interpolated by a fixed ratio and then decimated under control of a second sigma-delta modulated frequency selection signal that represents, on average, the data rate of the digital data to be output by the converter. The first and second frequency signal selection numbers are modulated using n-th order m-bit sigma-delta modulators. The method and apparatus converts the data rate of the incoming digital data stream to the data rate of the first n-th m-bit sigma-delta modulator and then converts the digital data stream from the first sigma-delta modulator (20) to an output data rate determined by the second n-th order m-bit sigma-delta modulator (32).
1. A digital to digital converter system, comprising:first interpolation means for receiving a digital signal having a first data rate and for supplying a digital signal having a first increased data rate; first decimation means, coupled to the interpolation means, for decimating the digital signal having the first increased data rate to provide a digital signal having a second data rate; first sigma-delta modulator means, coupled to and controlling the first interpolation means, for providing a first modulated output signal representative of the first data rate and for controlling the first interpolation means to provide the digital signal having the first increased data rate; second interpolation means, coupled to the first decimation means, for receiving the digital signal having the second data rate and for supplying a digital signal having a second increased data rate; second decimation means, coupled to the second interpolation means, for decimating the digital signal having the second increased data rate to provide a digital signal having a third data rate; and second sigma-delta modulator means, coupled to and controlling the second decimation means, for providing a second modulated output signal representative of the third data rate and for controlling the second decimation means to provide the digital signal having the third data rate. 2. The digital to digital converter system of claim 1, wherein the first sigma-delta modulator modulates a sampling frequency select signal representative of the first data rate.
3. The digital to digital converter system of claim 2, wherein the second sigma-delta modulator modulates a sampling frequency select signal representative of the third data rate.
4. The digital to digital converter system of claim 3, wherein the first interpolation means interpolates the digital signal having the first data rate by a ratio determined by the sampling frequency select-signal representative of the first data rate to provide the digital signal having the first increased data rate.
5. The digital to digital converter system of claim 4, wherein the first decimation means decimates the digital signal having the first increased data rate by a fixed ratio.
6. The digital to digital converter system of claim 5, wherein the second interpolation means interpolates the digital signal having the second data rate by a fixed ratio.
7. The digital to digital converter system of claim 6, wherein the second decimation means decimates the digital signal having the second increased data rate by a ratio determined by the sampling frequency select signal representative of the third data rate to provide the digital signal having the third data rate.
8. The digital to digital converter system of claim 7, further comprising a first clock generator means, coupled to the first modulator means, for generating, in response to the first modulated output signal, a clock having a frequency representative of the first data rate.
9. The digital to digital converter of claim 8, further comprising a second clock generator means, coupled to the second modulator means, for generating, in response to the second modulated output signal, a clock having a frequency representative of the third data rate.
10. The digital to digital converter system of claim 3, wherein the first interpolation means interpolates the digital signal having the first data rate by a fixed ratio.
11. The digital to digital converter system of claim 1, further comprising a memory means for storing a plurality of frequency selection numbers representative of at least one of the first and third data rate and means for selecting one of the frequency selection numbers in response to a selection signal and for providing the selected number to at least one of the first and second sigma-delta modulators as the sampling frequency select signal.
12. The digital to digital converter system of claim 11, wherein the first decimation means decimates the digital signal having the first increased data rate by a ratio determined by the sampling frequency select signal representative of the first data rate to provide the digital signal having the second data rate.
13. The digital to digital converter system of claim 12, wherein the second interpolation means interpolates the digital signal having the second data rate by a ratio determined by the sampling frequency select signal representative of the third data rate to provide the digital signal having the second increased data rate.
14. The digital to digital converter system of claim 13, wherein the second decimation means decimates the digital signal having the second increased data rate by a fixed ratio.
15. The digital to digital converter of claim 1, further comprising:first phase locked loop means, coupled to the first sigma-delta modulator means, for receiving a signal representative of the first data rate, locking to the signal, and providing a first control signal to the first sigma-delta modulator means that controls the first sigma-delta modulator means to provide the first sigma-delta modulated output signal. 16. The digital to digital converter of claim 1 or 15, further comprising:second phase locked loop means, coupled to the second sigma-delta modulator means, for receiving a signal representative of the third data rate, locking to the signal, and providing a control signal to the second sigma-delta modulator means that controls the second sigma-delta modulator means to provide the second sigma-delta modulated output signal. 17. The digital to digital converter of claim 15, further comprising:second phase locked loop means, coupled to the second sigma-delta modulator means, for receiving a signal representative of the third data rate, locking to the signal, and providing a control signal to the second sigma-delta modulator means that controls the second sigma-delta modulator means to provide the second sigma-delta modulated output signal. 18. The digital to digital converter system of claim 1, wherein the first and second modulated output signals are multi-bit codes.
19. The digital to digital converter system of claim 1, wherein the first and second sigma-delta modulators are nth -order modulators wherein n≧1.
20. The digital to digital converter system of claim 1, further comprising a filter means, coupled between the first decimation means and the second interpolation means, for filtering out noise and images of the digital signal having the first data rate.
21. A method of converting a first digital signal to a second digital signal, comprising the steps of:receiving a digital signal having a first data rate; sigma-delta modulating a first control signal to provide a first modulated output signal representative of the first data rate; increasing the first data rate to provide a digital signal having a first increased data rate; decimating the digital signal having the first increased data rate in response to the first modulated output signal to provide a digital signal having a second data rate; sigma-delta modulating a second control signal to provide a second modulated output signal representative of a third data rate; increasing the second data rate to provide a digital signal having a second increased data rate in response to the second modulated output signal; and decimating the digital signal having the second increased data rate to provide a digital signal having the third data rate. 22. The method of claim 21, wherein the step of increasing the first data rate includes increasing the first data rate by a fixed ratio.
23. The method of claim 22, wherein the step of decimating the digital signal having the first increased data rate includes decimating the digital signal having the first increased data rate by a ratio determined by the first modulated output signal.
24. The method of claim 23, wherein the step of increasing the second data rate includes increasing the second data rate by a ratio determined by the second modulated output signal.
25. The method of claim 24, wherein the step of decimating the digital signal having the second increased data rate includes decimating the second increased data rate by a fixed ratio.
26. A method of converting a first digital signal to a second digital signal, comprising the steps of:receiving a digital signal having a first data rate; sigma-delta modulating a first control signal to provide a first modulated output signal representative of the first data rate; increasing the first data rate to provide a digital signal having a first increased data rate in response to the first modulated output signal; decimating the digital signal having the first increased data rate to provide a digital signal having a second data rate; sigma-delta modulating a second control signal to provide a second modulated output signal representative of a third data rate; increasing the second data rate to provide a digital signal having a second increased data rate; and decimating the digital signal having the second increased date rate in response to the second modulated output signal to provide a digital signal having the third data rate. 27. The method of claim 26, wherein the step of increasing the first data rate includes increasing the first data rate by a ratio determined by the first modulated output signal.
28. The method of claim 27, wherein the step of decimating the digital signal having the first increased data rate includes decimating the digital signal having the first increased data rate by a fixed ratio.
29. The method of claim 28, wherein the step of increasing the second data rate includes increasing the second data rate by a fixed ratio.
30. The method of claim 29, wherein the step of decimating the digital signal having the second increased data rate includes decimating the digital signal having the second increased data rate by a ratio determined by the second modulated output signal.
31. The method of claim 21 or 26, further comprising the step of filtering the digital signal having the second data rate.
32. A digital to digital converter system, comprising:first interpolation means for receiving a digital signal having a first data rate and for supplying a digital signal having a first increased data rate; first decimation means, coupled to the interpolation means, for decimating the digital signal having the first increased data rate to provide a digital signal having a second data rate; first sigma-delta modulator means, coupled to and controlling the first decimation means, for providing a first modulated output signal representative of the first data rate and for controlling the decimation means to provide the digital signal having the second data rate; second interpolation means, coupled to the first decimation means, for receiving the digital signal having the second data rate and for supplying a digital signal having a second increased data rate; second decimation means, coupled to the second interpolation means, for decimating the digital signal having the second increased data rate to provide a digital signal having a third data rate; second sigma-delta modulator means, coupled to and controlling the second interpolation means, for providing a second modulated output signal representative of the third data rate and for controlling the second interpolation means to provide the digital signal having the second increased data rate; and further comprising a memory means for storing a plurality of frequency selection numbers representative of at least one of the first and third data rate and means for selecting one of the frequency selection numbers in response to a selection signal and for providing the selected number to at least one of the first and second sigma-delta modulators as the sampling frequency select signal. 33. The digital to digital converter system of claim 32, wherein the first decimation means decimates the digital signal having the first increase data rate by a ratio determined by the sampling frequency select signal representative of the first data rate to provide the digital signal having the second data rate.
34. The digital to digital converter system of claim 33, wherein the second interpolation means interpolates the digital signal having a second data rate by a ratio determined by the sampling frequency select signal representative of the third data rate to provide the digital signal having the second increased data rate.
35. The digital to digital converter system of claim 34, wherein the second decimation means decimates the digital signal having the second increased data rate by a fixed ratio.
36. A digital to digital converter system, comprising:first interpolation means for receiving a digital signal having a first data rate and for supplying a digital signal having a first increased data rate; first decimation means, coupled to the interpolation means, for decimating the digital signal having the first increased data rate to provide a digital signal having a second data rate; first sigma-delta modulator means, coupled to and controlling the first decimation means, for providing a first modulated output signal representative of the first data rate and for controlling the decimation means to provide the digital signal having the second data rate; second interpolation means, coupled to the first decimation means, for receiving the digital signal having the second data rate and for supplying a digital signal having a second increased data rate; second decimation means, coupled to the second interpolation means, for decimating the digital signal having the second increased data rate to provide a digital signal having a third data rate; and second sigma-delta modulator means, coupled to and controlling the second interpolation means, for providing a second modulated output signal representative of the third data rate and for controlling the second interpolation means to provide the digital signal having the second increased data rate; wherein the first sigma-delta modulator modulates a sampling frequency select signal representative of the first data rate. 37. The digital to digital converter system of claim 36, wherein the second sigma-delta modulator modulates a sampling frequency select signal representative of the third data rate.
38. The digital to digital converter of claim 37, wherein the first interpolation means interpolates the digital signal having the first data rate by a fixed ratio.
39. A digital to digital converter system, comprising:first interpolation means for receiving a digital signal having a first data rate and for supplying a digital signal having a first increased data rate; first decimation means, coupled to the interpolation means, for decimating the digital signal having the first increased data rate to provide a digital signal having a second data rate; first sigma-delta modulator means, coupled to and controlling the first decimation means, for providing a first modulated output signal representative of the first data rate and for controlling the decimation means to provide the digital signal having the second data rate; second interpolation means, coupled to the first decimation means, for receiving the digital signal having the second data rate and for supplying a digital signal having a second increased data rate; second decimation means, coupled to the second interpolation means, for decimating the digital signal having the second increased data rate to provide a digital signal having a third data rate; and second sigma-delta modulator means, coupled to and controlling the second interpolation means, for providing a second modulated output signal representative of the third data rate and for controlling the second interpolation means to provide the digital signal having the second increased data rate; wherein the first and second modulated output signals are multi-bit codes. 40. The digital to digital converter system of claim 39, further comprising a filter means, coupled between the first decimation means and the second interpolation means, for filtering out noise and images of the digital signal having the first data rate.
41. A method of combining at least two digital signals, comprising the steps of:receiving a digital signal having a first data rate; converting the digital signal having the first data rate to a first digital signal having a second data rate in response to a first sigma-delta modulated control signal; receiving a digital signal having a third data rate; converting the digital signal having the third data rate to a second digital signal having the second data rate in response to a second modulated control signal; combining the first digital signal having the second sigma-delta data rate and the second digital signal having the second data rate into a single digital signal having the second data rate. 42. A method of providing at least two digital signals from a single digital signal, comprising the steps of:receiving a digital signal having a first data rate; converting the digital signal having a first data rate to a digital signal having a second data rate in response to a first sigma-delta modulated control signal; converting the digital signal having the first data rate to a digital signal having a third data rate in response to a second sigma-delta modulated control signal; outputting the digital signal having the second data rate; and outputting the digital signal having the third data rate. 43. An apparatus for combining at least two digital signals, comprising:means for receiving a digital signal having a first data rate; means for converting the digital signal having the first data rate to a first digital signal having a second data rate in response to a first sigma-delta modulated control signal; means for receiving a digital signal having a third data rate; means for converting the digital signal having the third data rate to a second digital signal having the second data rate in response to a second sigma-delta modulated control signal; and means for combining the first digital signal having the second data rate and the second digital signal having the second data rate into a single digital signal having the second data rate. 44. An apparatus for providing at least two digital signals from a single digital signal, comprising:means for receiving a digital signal having a first data rate; means for converting the digital signal having the first data rate to a digital signal having a second data rate in response to a first sigma-delta modulated control signal; means for converting the digital signal having the first data rate to a digital signal having a third data in response to a second sigma-delta modulated control signal; means for outputting the digital signal having the second data rate; and means for outputting the digital signal having the third data rate. 45. A digital to digital converter system, comprising:means for converting a digital signal having a first data rate to a digital signal having a second data rate in response to a first sigma-delta modulated control signal; and means for converting the digital signal having the second data rate to a digital signal having a third data rate in response to a second sigma-delta modulated control signal. 46. A method of converting a first digital signal to a second digital signal, comprising the steps of:converting a digital signal having a first data rate to a digital signal having a second data rate in response to a first sigma-delta modulated control signal; and converting a digital signal having the second data rate to a digital signal having a third data rate in response to a second sigma-delta modulated control signal. 47. A digital to digital converter system, comprising:first interpolation means for receiving a digital signal having a first data rate and for supplying a digital signal having a first increased data rate; first decimation means, coupled to the interpolation means, for decimating the digital signal having the first increased data rate to provide a digital signal having a second data rate; first sigma-delta modulator means, coupled to and controlling the first decimation means, for providing a first modulated output signal representative of the first data rate and for controlling the decimation means to provide the digital signal having the second data rate; second interpolation means, coupled to the first decimation means, for receiving the digital signal having the second data rate and for supplying a digital signal having a second increased data rate; second decimation means, coupled to the second interpolation means, for decimating the digital signal having the second increased data rate to provide a digital signal having a third data rate; and second sigma-delta modulator means, coupled to and controlling the second interpolation means, for providing a second modulated output signal representative of the third data rate and for controlling the second interpolation means to provide the digital signal having the second increased data rate; wherein the first and second sigma-delta modulators are nth -order modulators wherein n>1. Description
This application is a continuation-in-part of our application Ser. No. 08/120,957, filed Sep. 13, 1993, entitled DIGITAL TO ANALOG CONVERSION USING NONUNIFORM SAMPLE RATES now abandoned, application Ser. No. 08/121,104, filed Sep. 13, 1993, entitled ANALOG TO DIGITAL CONVERSION USING NONUNIFORM SAMPLE RATES now abandoned, application Ser. No. 08/241,059, filed May 11, 1994, entitled DIGITAL TO DIGITAL CONVERSION USING NONUNIFORM SAMPLE RATES, International Application Ser. No. PCT/US94/10268, filed Sep. 13, 1994, entitled ANALOG TO DIGITAL CONVERSION USING NONUNIFORM SAMPLE RATES, and International Application Ser. No. PCT/US94/10269, filed Sep. 13, 1994, entitled DIGITAL TO ANALOG CONVERSION USING NONUNIFORM SAMPLE RATES, the disclosures of which are incorporated herein by reference in their entirety.
The present invention relates generally to the field of methods and circuits for digital-to-digital conversion. More particularly, the present invention relates to a method and circuit for digital-to-digital signal conversion using sigma-delta modulation of the temporal spacing between digital samples.
Digital-to-digital converter circuits and methods for digital-to-digital conversion are well-known in the art. One example of a conventional digital-to-digital converter is the AD1890/AD1891 asynchronous sample rate converter, manufactured by Analog Devices, Incorporated, One Technology Way, P.O. Box 9106, Norwood, Mass., 02062. Conceptually, these converters interpolate the input data up to a very high equivalent internal sample rate with a time resolution of 300 picoseconds and then decimate the interpolated data down to the desired output sample rate. The equivalent frequency of the oversampled digital data is approximately 3.2768 gigahertz. FIG. 1 is an overall functional block diagram of the AD 1890/1891. As shown in FIG. 1, the input digital data at a data rate Fs1 is interpolated at some ratio by inserting zero valued samples between each of the original input signal samples by the interpolator. The oversampled signal is then fed into a digital FIR low-pass filter to smooth or integrate the sequence. The interpolated and filtered digital data is then passed to a zero-order hold register and then asynchronously resampled by decimating the digital data stream in the decimation block to produce the digital data out at a data rate Fs2.
One of the limitations of conventional digital-to-digital converters is that they only determine the magnitude of the input signal at equally spaced temporal intervals. This is known as uniform sampling. Additionally, in conventional digital-to-digital converters, the sample rate, that is, the rate of the incoming digital data stream cannot be independent of the master clock that is used to clock the digital-to-digital converter. The incoming digital data rate must be some integer division of the master clock of the digital-to-digital converter chip. This means that if the digital-to-digital converter were to receive digital data at two different data rates, that are not necessarily divisible into the master clock (or more generally, digital data at a rate that is not integrally divisible into the master clock), there must be two different frequency master clocks available for clocking the digital-to-digital converter (or more generally, there must be a master clock that has an integer relationship with the data rate of the incoming digital data available to clock the digital-to-digital converter).
Another problem with conventional digital-to-digital converters is that they are typically not designed to be clocked by an externally supplied clock signal. The components of the digital-to-digital converter are typically optimized to operate at the clock frequency determined by the master clock on the digital-to-digital converter chip. This leads to the additional limitation that some digital-to-digital converters cannot lock to and operate at some externally supplied clock signal. Therefore, if there are any changes in the digital data rate, since the incoming digital data stream and the master clock for the digital-to-digital converter are not necessarily related to each other, any temporal changes in the relative frequencies of the incoming digital data rate and the master clock can disrupt the entire digital-to-digital conversion process.
In addition, the number of FIR filter taps and associated coefficients can become so large as to make the filter complicated and difficult to obtain a high throughput when the incoming digital data stream has a fast data rate.
Therefore, an object of the present invention is to provide a method and apparatus for performing digital-to-digital conversion using NONUNIFORM sampling (i.e., variable temporal spacing of the sampling points).
Another object of the present invention is to provide a method and apparatus for performing digital-to-digital conversion that can lock to an externally supplied clock signal and can provide a sampling rate that is independent of the converter's master clock.
The present invention overcomes the limitations of the prior art by providing a method and apparatus for digital-to-digital conversion using NONUNIFORM sampling. In one embodiment of the invention, the apparatus includes a first interpolator or other comparable circuitry such as a sample and hold circuit for receiving digital signals at a first data rate and for supplying the digital signals at a first increased data rate and a first decimator, coupled to the first interpolator, for decimating the digital signals at the first increased data rate to provide digital signals at a second data rate. In one embodiment, a first sigma-delta modulator is coupled to and controls the first decimator and provides a first sigma-delta modulated output signal representative of the first data rate and controls the first decimator to provide the digital signals at the second data rate. This part of the invention interpolates digital data by a fixed ratio and then decimates the interpolated digital data by a variable ratio depending on the second data rate desired. In another embodiment, a sigma-delta modulator is coupled to and controls the interpolator and provides a sigma-delta modulated output signal representative of the first data rate and controls the interpolator to provide a digital data stream at the increased data rate so that, upon decimation by the decimator, the digital signals are at the second rate. This part of the invention interpolates the digital data by a variable ratio depending on the second data rate desired and then decimates the interpolated data by a fixed ratio. Depending on the performance requirements of the particular application, the decimated digital data at the second data rate may then be filtered to remove, for example, sigma-delta noise introduced by the variable decimation of the digital data at the first increased data rate.
The digital data at the second data rate is supplied to a second interpolator or other comparable circuitry such as a sample and hold circuit that receives the digital data at the second data rate and supplies the digital signals at a second increased data rate. A second decimator is coupled to the interpolator and decimates the digital signals at the second increased data rate to provide digital signals at a third data rate. In one embodiment, a second sigma-delta modulator is coupled to and controls the second interpolator and provides a second sigma-delta modulated output signal representative of the third data rate to control the second interpolator to provide the digital signals at the second increased data rate so that, upon decimation by the second decimator, the digital signals are at the third data rate. This part of the invention interpolates the digital data by a variable ratio depending on the third data rate desired and then decimates the interpolated digital data by a fixed ratio. In another embodiment, a sigma-delta modulator is coupled to and controls the decimator and provides a sigma-delta modulated output signal representative of the third data rate and controls the decimator to provide the digital signals at the third data rate. This part of the invention interpolates the digital data by a fixed ratio and then decimates the interpolated digital data by a variable ratio depending on the third data rate desired.
In another embodiment of the invention, a first phase locked loop (PLL) which may be a digital PLL or may be an analog PLL having its output coupled to the first sigma-delta modulator is provided for receiving a signal representative of the first data rate, locking to the signal, and providing a first control signal to the first sigma-delta modulator that controls the first sigma-delta modulator to provide the sigma-delta modulated output signal. In one embodiment, the first sigma-delta modulator forms part of the digitally controlled oscillator in the PLL. The first phase locked loop allows the circuit to lock to and track any externally-supplied clock signal.
In another embodiment of the invention, a second phase locked loop (PLL) which may be a digital PLL or may be an analog PLL having its output coupled to the second sigma-delta modulator is provided for receiving a signal representative of the third data rate, locking to the signal, and providing a second control signal to the second sigma-delta modulator that controls the second sigma-delta modulator to provide the second sigma-delta modulated output signal. The second sigma-delta modulator forms part of the digitally controlled oscillator in the PLL. The second phase locked loop allows the circuit to lock to and track any externally-supplied clock signal.
Broadly stated, the method of the present invention includes sigma-delta modulation of the time base such that errors produced by NONUNIFORM sampling are frequency-shaped to a region (i.e., shifted to higher frequencies) where they can be removed by conventional filtering techniques. That is, the present invention provides temporally noise-shaped digital signals.
In one part of the invention, the method is to perform a fixed interpolation (or other method of increasing the data rate or sample rate of the digital signal or digital data stream) and filtering to remove images followed by variable decimation with the decimation controlled by a first sigma-delta modulator that is fed a frequency selection signal representing the sampling frequency or data rate of the input data stream. Fixed interpolation means that the interpolation ratio is the same regardless of the sample rate. Variable decimation means that the decimation ratio is varied as a function of the desired output sample rate. More particularly, a digital data stream at a data rate within some predetermined limits is interpolated to a higher data rate. This higher data rate digital data stream is then decimated using a control signal that is a sigma-delta modulated signal that represents the data rate of the incoming digital data stream. The frequency selection signal is modulated using a first n-th order m-bit sigma-delta modulator. This control signal (the sigma-delta modulated frequency selection number output by the second sigma-delta modulator) represents, on average, the data rate of the incoming digital data stream. Data thus emerges from the interpolation/decimation process at the clock rate of the first n-th order m-bit sigma-delta modulator.
This part of the method thus converts the data rate of the incoming digital data stream to the data rate of the first n-th order m-bit sigma-delta modulator.
Once the data rate of the incoming digital data stream has been converted to the data rate of the first n-th order m-bit sigma-delta modulator, another part of the method is to perform a variable interpolation (or other method to increase the data rate or sampling frequency of the digital signal or digital data stream) and filtering to remove images followed by a fixed decimation with the interpolation controlled by a second sigma-delta modulator that is fed a frequency selection signal representing the desired output sample rate. Variable interpolation means that the interpolation ratio is varied as a function of the desired output sample rate. Fixed decimation means that the decimation ratio is the same regardless of the sample rate. More particularly, the digital data stream at the data rate of the first n-th order m-bit sigma-delta modulator is interpolated to a higher data rate using a control signal that is a sigma-delta modulated signal that represents the desired output data rate (i.e., sample rate or sampling frequency). The frequency selection signal is modulated using a second n-th order m-bit sigma-delta modulator. This control signal (the sigma-delta modulated frequency selection signal output by the second sigma-delta modulator) represents, on average, the sample rate of the digital data to be output by the converter. The control signal controls the interpolator to increase the data rate such that, upon fixed decimation, data emerges from the interpolation/decimation process at the desired output sample rate.
This part of the method thus converts the data rate of the digital data stream output by the variable decimation process from an oversampled signal to a digital data stream having the desired sample rate.
In another part of the invention, the method is to perform a variable interpolation (or other method to increase the sample rate of the digital data stream) and filtering to remove images followed by a fixed decimation with the interpolation controlled by a sigma-delta modulator that is fed a frequency selection number representing the sampling frequency of the input data stream. Variable interpolation means that the interpolation ratio is varied as a function of the desired output sample rate. Fixed decimation means that the decimation ratio is the same regardless of the sample rate. A digital data stream at a data rate within some predetermined limits is interpolated to a higher data rate using a control signal that is a sigma-delta modulated signal that represents the data rate of the incoming digital data stream. The frequency selection signal is modulated using an n-th order m-bit sigma-delta modulator. This control signal (the sigma-delta modulated frequency selection number output by the sigma-delta modulator) represents, on average, the data rate of the incoming digital data stream. The control signal controls the interpolator to increase the data rate such that, upon fixed decimation, data emerges from the interpolation/decimation process at the clock rate of the n-th order m-bit sigma-delta modulator.
The part of the method thus convert the data rate of the incoming digital data stream to the data rate of the n-th order m-bit sigma-delta modulator.
Once the data rate of the incoming digital data stream has been converted to the data rate of the first n-th order m-bit sigma-delta modulator, another part of the method is to perform a fixed interpolation (or other method to increase the sample rate of the digital data stream) and filtering to remove images followed by a variable decimation with the decimation controlled by a second sigma-delta modulator that is fed a frequency selection number representing the desired sample rate of the output digital data stream. Fixed interpolation means that the interpolation ratio is the same regardless of the sample rate. Variable decimation means that the decimation ratio is varied as a function of the desired output sample rate. More particularly, a digital data stream at the data rate of the first n-th order m-bit sigma-delta modulator is interpolated to higher data rate. This higher data rate digital data stream is then decimated using a control signal that is a sigma-delta modulated signal that represents the desired output data rate (or sample rate). The frequency selection signal is modulated using a second n-th order m-bit sigma-delta modulator. This control signal (the sigma-delta modulated frequency selection signal output by the sigma-delta modulator) represents, on average, the sample rate of the digital data to be output by the converter. Data thus emerges from the interpolation/decimation process at the desired output sample rate.
The part of the method thus converts the data rate of the digital data stream output by the variable interpolation process from an oversampled signal to a digital data stream having the desired sample rate.
FIG. 1 is a block diagram of a conventional digital-to-digital converter;
FIG. 2 is a block diagram of a digital-to-digital converter circuit incorporating a first embodiment of the invention;
FIG. 4 is a block diagram of a circuit for supplying previously stored frequency numbers to the n-th order m-bit sigma-delta modulator of FIGS. 2-3, 5-5A, 9-10, 12, and 14-17;
FIG. 5 is a block diagram illustrating a locking circuit in the circuits of FIGS. 2-3 and 16-17;
FIG. 5A is a block diagram illustrating the use of a combination of a locking circuit and a sigma-delta modulator in the circuits of FIGS. 2-3 and 16-17;
FIG. 6 is a block diagram of a locking circuit that may be used in conjunction with the circuits of FIGS. 2-3, 5-5A, 9-10, 12, and 14-17, to lock the digital-to-digital converter to an externally supplied clock signal;
FIG. 7 is a block diagram of a second locking circuit that may be used in conjunction with the circuits of FIGS. 2-3, 5-5A, 9-10, 12, and 14-17, to lock the digital-to-digital converter to an externally supplied clock signal;
FIG. 8 is a flow chart illustrating the steps of a first embodiment of the method of the present invention;
FIG. 9 is a block diagram of a digital-to-digital converter circuit incorporating a second embodiment of the invention;
FIG. 11 is a flow chart illustrating the steps of a second embodiment of the method of the present invention;
FIG. 12 is a block diagram of a digital-to-digital converter circuit incorporating a third embodiment of the invention;
FIG. 13 is a graph illustrating the relationship between the four-bit codes and the corresponding sampling frequency in the circuit of FIG. 12;
FIG. 14 is a block diagram illustrating a locking circuit in the circuits of FIGS. 9-10, 12, and 14-17;
FIG. 15 is a block diagram illustrating the use of a combination of a locking circuit and a sigma-delta modulator in the circuits of FIGS. 9-10, 12, and 14-17;
FIG. 16 is a block diagram illustrating a circuit that provides for digitally mixing signals that may have differing sample rates;
FIG. 17 is a block diagram illustrating a circuit for providing, from a digital data stream having one data rate, digital data streams that may have differing data rates;
FIG. 18 is a flow chart illustrating the steps of the method of digitally mixing signals of the present invention; and
FIG. 19 is a flow chart illustrating the steps of the method of providing multiple digital data streams from one digital data stream in accordance with the present invention.
FIG. 2 is a block diagram broadly illustrating a first embodiment of the invention. The overall purpose of circuit 10 is to receive a digital data stream on line 12 at any data rate within a predetermined working range of the system and to convert the digital data to a digital data stream on line 42. The data rate of the digital data stream on line 42 can be the same as, higher, or lower than the data rate of the digital data stream on line 12.
Circuit 10 performs this function by increasing the sample rate (Fs1) of the digital data stream on line 12 to create a first so-called "oversampled" signal and then decimates this higher rate data stream so that the data stream presented on line 14 is at a fixed, predetermined data rate. In other words, circuit part 13 of circuit 10 receives digital data at any data rate within the predetermined working range of the system, and converts this data to a digital data stream on line 14 at another data rate. The data rate on line 14 may or may not be the same as the data rate of the input data stream and may be a fixed or a variable rate. The digital data stream on line 12 may be of any width (i.e., any number of bits). Once the digital data on line 12 has been converted to the predetermined data rate on line 14, circuit 10 increases the sample rate of the digital data on line 14 to create a second so-called "oversampled" signal and then decimates this higher rate digital data stream so that the data presented on line 42 is at a desired output sampling rate. In other words, circuit part 15 of circuit 10 receives digital data at the fixed, predetermined data rate and converts this data to a digital data stream at another data rate.
In circuit part 13 of the circuit 10 illustrated in FIG. 2, an interpolator 16 receives the digital data stream on line 12 at any data rate (Fs1) within the predetermined working range. Interpolator 16 increases the sample rate of the digital data stream (that is, converts the digital data stream into a higher sample rate digital data stream) on line 12 by, for example, inserting zeros between data samples, in a manner well-known to those skilled in the art. One skilled in the art will appreciate that other techniques may be used for increasing the sample rate of the data stream on line 12, such as sample and hold techniques. The purpose of interpolator 16 is to increase the sample rate of the digital data stream on line 12 to create an oversampled signal. A higher sample rate digital data stream 17 is then sent to a digital filter 18 which attenuates any images of the original digital signal as a result of the interpolation process. The filtered digital data stream on line 19 is then sent to a decimation block 21 that decimates digital data stream on line 19 under control of the sigma-delta modulator 20. Although filter 18 and decimation block 21 have been illustrated as separate circuit elements for illustrative purposes, one skilled in the art will appreciate that these functions may be performed by a single computational element, such as an FIR or IIR filter in a well-known manner.
The sigma-delta modulator 20 produces digital data at the frequency of clock 22, the data controlling the decimation of decimation block 21. As will be explained in more detail hereinafter, the sigma-delta modulator 20 sigma-delta modulates a signal 24 representative of the data rate (Fs1) of the digital data stream on line 12. An example will serve to illustrate this function. Assume that the data rate of the data stream on line 12 is 48 kHz. Interpolator 16 increases this data rate to 18.432 mHz by interpolating the data by a factor of 384. Assume the frequency of clock 22 is 3.072 mHz. Since the data rate of data stream 12 is 48 kHz, signal 24 is therefore a multi-bit digital number representative of a sampling rate of 48 kHz where the number of bits in the digital number control the precision with which the data rate of digital data stream on line 12 can be specified. This digital number is sigma-delta modulated by the sigma-delta modulator 20 and used to control decimation block 21 to produce one output signal for every six samples in digital data stream 19. The 18.432 mHz data is then effectively decimated by a factor of six and the digital data stream on line 14 is therefore at, on average, a 3.072 mHz data rate.
Sigma delta modulator 20 is preferably an n-th order m-bit sigma-delta modulator. The higher the order of the sigma-delta modulator, the better the noise shaped characteristics of the output signal on line 26. The signal on line 26 output by sigma-delta modulator 20 is chosen to be m-bits (where m≧1 and is more than one bit in a preferred embodiment) because, as the number of bits is increased, the clock rate necessary to operate sigma-delta modulator 20 can be reduced. However, it is to be appreciated that the invention is not so limited. Sigma-delta modulator 20 could also be a one bit modulator if the clock frequency used to run the modulator is increased as necessary.
A key feature of the present invention as a whole and in particular circuit part 13 is that the temporal spacing of the sampling points is controlled by the n-th order m-bit sigma-delta modulator such that any errors (i.e., noise on the sampling points) produced by this NONUNIFORM sampling are shaped in the frequency domain. That is, the digital signal output by the present invention as well as the control signal produced by the sigma-delta modulator are temporally noise-shaped. All embodiments of the invention provide this feature. As is well-known in the field of sigma-delta systems, this noise on the digital signal produced by circuit part 15 produced by errors resulting from the NONUNIFORM sampling can be removed by conventional digital filtering techniques.
Several other advantages are also obtained. By appropriate choice of the rate at which the sigma-delta spaced sampling points are generated and the number of bits used in controlling the spacing of these sampling points, the signal to noise ratio of the digital data stream on line 14 can be controlled. Further degrees of freedom are available by varying the order of the sigma-delta modulator used to control the oversampling ratio. In another aspect of the invention, the degree of filtering used on the digital data stream on line 17 can also be varied to vary the signal-to-noise ratio as well.
The digital data at the predetermined data rate on line 14 is optionally filtered by a filter 11 depending on the performance requirements of the particular application. Filter 11 removes any sigma-delta noise on the digital data stream on line 14 as a result of the sigma-delta modulator's control of decimation block 21. Filter 11 may be a sinc-type filter, such as a sinc 964 filter, well known to those skilled in the art. The filtered data from filter 11 on line 28 is sent to circuit part 15 of circuit 10.
In circuit part 15 of the circuit 10 illustrated in FIG. 2, the filtered digital data stream on line 28 is then sent to interpolator 30. Interpolator 30 increases the sample rate of the digital data stream (that is, converts the digital data stream into a higher sample rate digital data stream) on line 28 by using a sample and hold technique that repeats the digital sample for a specified number of clock cycles in a manner well-known to those skilled in the art. One skilled in the art will appreciate that other techniques may be used for increasing the sample rate of the data stream on line 28, such as interpolation techniques that insert zeroes between data samples. The purpose of interpolator 30 is to increase the sample rate of the digital data stream on line 28 to create an oversampled signal.
The interpolation ratio (i.e., the ratio by which the sample rate of the digital data on line 28 is increased by interpolator 30) is controlled by a sigma-delta modulator 32. Sigma-delta modulator 32 may be the same type of modulator as sigma-delta modulator 20.
A higher sample rate digital data stream on line 34 is then sent to a digital filter 36 which removes any images of the original digital signal as a result of the interpolation process. The filtered digital data stream on line 38 is then sent to a decimation block 40 that decimates the digital data stream on line 38 by a fixed decimation ratio to produce the digital data stream on line 42 having a sample rate (Fs2) selected by a sampling frequency select signal 44. Although filter 36 and decimation block 40 have been illustrated as separate circuit elements for illustrative purposes, one skilled in the art will appreciate that these functions may be performed by a single computational element, such as an FIR or IIR filter in a well known manner.
The sigma-delta modulator 32 produces digital data at the frequency of clock 22, the data controlling the interpolation of interpolator 30. As will be explained in more detail hereinafter, the sigma-delta modulator 32 sigma-delta modulates a signal 44 representative of the desired output sample rate (Fs2) of the digital data stream on line 42. An example will serve to illustrate this function. Assume that the data rate of the digital data stream on line 28 is 3.072 mHz. Assume the frequency of clock 22 is 3.072 mHz. If the desired data rate of the data stream on line 42 is 32 kHz, signal 44 is therefore a multi-bit digital number representative of a sampling rate of 32 kHz where the number of bits in the digital number control the precision with which the data rate (Fs2) of the data stream on line 42 can be specified. This digital number is sigma-delta modulated by the sigma-delta modulator 32 and used to control interpolator 30 to increase the sample rate of the digital data stream on line 28 by a factor of four. Interpolator 28 increases this data rate to 12.288 mHz by interpolating the data by a factor of four. The resulting 12.288 mHz data is then decimated, after filtering by filter 36, by a factor of 384 (decimator 40 having a decimation ratio of 384) and the digital data stream emerging on line 42 is therefore at, on average, a 32 kHz data rate.
Sigma-delta modulator 32 is preferably an n-th order m-bit sigma-delta modulator. The higher the order of the sigma-delta modulator, the better the noise shaped characteristics of the output signal on line 42. The signal on line 46 output by sigma-delta modulator 32 is chosen to be m-bits (where m≧1 n and is more than one bit in a preferred embodiment) because, as the number of bits which control interpolator 30 is increased, the clock rate necessary to operate sigma-delta modulator 32 can be reduced. However, it is to be appreciated that the invention is not so limited. Sigma-delta modulator 32 could also be a one bit modulator if the clock frequency used to run the modulator is increased as necessary.
A key feature of the present invention is as a whole (as discussed previously) and circuit part 15 in particular that the temporal spacing of the sampling points is controlled by the n-th order m-bit sigma-delta modulator such that any errors (i.e., noise on the sampling points) produced by this NONUNIFORM sampling are shaped in the frequency domain. That is, the digital signal output by the present invention as well as the control signal produced by the sigma-delta modulator are temporally noise-shaped. All embodiments of the invention provide this feature. As is well-known in the field of sigma-delta systems, this noise on the digital signal produced by circuit part 15 produced by errors resulting from the NONUNIFORM sampling can be removed by conventional digital filtering techniques.
Several other advantages are also obtained. By appropriate choice of the rate at which the sigma-delta spaced sampling points are generated and the number of bits used in controlling the spacing of these sampling points, the signal-to-noise ratio of the digital data stream on line 42 can be controlled. Further degrees of freedom are available by varying the order of the sigma-delta modulator used to control the oversampling ratio. In another aspect of the invention, the degree of filtering used on the digital data stream on line 34 can also be varied to vary the signal-to-noise ratio as well.
FIG. 3 illustrates a more detailed embodiment of the digital-to-digital converter of FIG. 2. In circuit 100, circuit part 51 is analogous to circuit part 13 in FIG. 2 and circuit part 90 is analogous to circuit part 15 in FIG. 2. In the circuit 100 of FIG. 2, an n-bit wide digital data stream on line 50 which may be, for example, in the range of 4 kHz to 48 kHz is received by interpolator 52. Interpolator 52 increases the sample rate (Fs1) of digital data stream on line 50 by a factor of four using, for example, a zero fill technique that inserts zeros between the digital samples. The higher sample rate signal output by interpolator 52 (now in the range of 16 kHz to 192 kHz) is then fed into a digital low pass filter 54 which may be, for example, a finite impulse response type filter. Low pass filter 54 filters out of band images of the digital signal on line 50 out of the digital data stream on line 53. The filtered digital data stream on line 56 from low pass filter 54 is then fed into interpolator 58 that increases the sample rate of the digital data stream on line 56 by a factor of ninety-six. Inserting ninety-five zeros into the digital data stream on line 56 will reduce the gain of the original signals because of the dilution of the signal by the inserted zeros. However, as is well-known, the parameters of filter 62 can be adjusted to compensate for this loss of gain. The higher sample rate digital data signal on line 60 (now in the range of 1.536 mHz to 18.432 mHz) provided by interpolator 58 is fed into digital filter 62.
In one embodiment, digital filter 62 is a sinc 964 -type filter that is designed to have zeros at the image frequencies of the digital data stream on line 60. Filter 62 could, however, be any type of IIR or FIR filter. In the embodiment illustrated in FIG. 3, digital filter 62 provides both a low pass filtering function and a decimation function. One skilled in the art will appreciate that these two functions could be separated in the manner illustrated in FIG. 2. As will be explained in greater detail hereinafter, filter 62 outputs a digital data stream on line 64 at 3.072 mHz.
It is to be noted that the digital data streams on lines 53, 56, 60, and 64 are indicated as being n-bits wide in FIG. 3. N may be any number of bits and is typically chosen to be the widest bit stream commensurate with the signal-to-noise ratio requirements of the particular application. Furthermore, the digital data streams may be different widths on each of the lines.
The n-th order m-bit sigma-delta modulator 66 provides a four-bit number on line 68 that controls filter 62 to produce the output data stream on line 64. Sigma-delta modulator 66 is, in one embodiment, a third order four-bit modulator. Sigma delta modulator 66 is clocked using a 3.072 mHz clock 70.
In one embodiment, a twenty-bit frequency selection number 72 (representing Fs1) is input into sigma-delta modulator 66N. Frequency selection number 72 ranges from -219 to +219. This twenty-bit number controls the precision with which the four-bit number output by sigma-delta modulator 66 represents the sampling rate (Fs1) of the input digital data stream on line 50. Sigma-delta modulator 66 modulates the twenty-bit number to produce sigma-delta modulated four-bit codes that control filter 62. The first bit of the code is a sign bit. The remaining three bits produce codes that direct the filter 62 to calculate and produce an output every P samples of the data stream on line 60, effectively sample rate converting the data stream.
Table 1 illustrates the relationship among the four-bit codes that are produced by sigma-delta modulator 66, the intervals at which filter 62 produces an output, and the sampling frequency that the four-bit code corresponds to when modulator 66 is clocked using a 3.072 mHz clock. Some examples will illustrate the operation of this part of the system.
TABLE 1______________________________________     PRODUCE AN     OUTPUT EVERY     P SAMPLES     CORRESPONDING     ALLOW P CLOCKS                   TO SAMPLING4 BIT CODE     TO PASS THROUGH                   FREQUENCY OF (kHZ)______________________________________+4        8             64+3        7             56+2        6             48+1        5             40 0        4             32-1        3             24-2        2             16-3        1              8-4        0             DC______________________________________
Assume, for purposes of illustration, that the digital data stream on line 50 has a data rate (Fs1) of 48 kHz. Interpolator 52 increases this data rate to 192 kHz. Interpolator 58 increases the 192 kHz sampling rate to 18.432 mHz. To produce the digital data stream on line 64 at 3.072 mHz at the output of filter 62 (i.e, at the clock rate of the clock controlling sigma-delta modulator 66), the digital data stream on line 60 at 18.432 mHz must be decimated by a factor of six. Therefore, twenty-bit frequency selection number 72 is selected such that upon sigma-delta modulation by the third order four-bit sigma-delta modulator 66, the four bit codes generated will be, on average, a +2 code although other four bit codes will be produced but with a lower frequency of occurrence.
A key point to remember is that the +2 code is the resulting average of all the codes produced by sigma-delta modulator 66 upon sigma-delta modulation of twenty-bit frequency selection number 72. A +2 code is not produced every time sigma-delta modulator 66 is clocked even though the input sample rate (Fs1) and the output sample rate of the data stream on line 64 are related to each other by an integer multiple. Even if the sample rates were related to each other by an integer multiple, any errors, no matter how small, that result in a temporal displacement between the sample points in the input digital data stream on line 50 and the sample points in the rate-converted digital data stream on line 64 would increase the signal-to-noise ratio to a point where the conversion process would not be acceptable. In the present invention, the time base (i.e., the temporal spacing between samples) is sigma-delta modulated so that the errors due to temporal displacement between the input and rate-converted digital data stream that cause noise are pushed into a higher frequency range. This noise is then removed by conventional filtering techniques such as in filter 74.
In another example, assume that the digital data stream on line 50 has a data rate (i.e., a sample rate or sampling frequency) (Fs1) of 4 kHz. Interpolator 52 increases this data rate to 16 kHz. Interpolator 58 increases the 16 kHz data rate to 1.536 mHz. In order that the digital data stream on line 64 have a data rate of 3.072 mHz (i.e., the clock rate of the clock controlling sigma-delta modulator 66), the digital data stream on line 60 at 1.536 mHz must be effectively interpolated by a factor of 2. Therefore twenty-bit frequency selection number 72 (representing Fs1) is chosen such that sigma-delta modulator 66 produces, on average, an equal number of -3 and -4 codes although other four bit codes will be produced, but with a lower frequency of occurrence. That is, occasionally, -2, -1, and even less frequently, +1, +2 codes will be produced. As shown in Table 1, the -3 code directs sinc filter 62 to produce an output for each input sample corresponding to a sampling frequency of 8 kHz for the clock frequencies and interpolation ratios illustrated.
One skilled in the art will appreciate that any sampling frequencies within the 0 to 64 kHz range may be produced by varying the ratio of four-bit codes produced by sigma-delta modulator 66. For example, to obtain a sampling frequency between 56 kHz and 64 kHz, the appropriate ratio of +3 and +4 codes would be output by sigma-delta modulator 66 as a function of twenty-bit number 72. One skilled in the art will also appreciate that any sample rate within the working range of the system can be produced through the appropriate combination of four-bit codes.
Although modulator 66 has been illustrated as a four-bit sigma-delta modulator, the invention is not so limited. For example, a sigma-delta modulator that outputs fewer bits can be used if the clock rate of the clock supplied to the modulator is increased as necessary. In the same manner, a sigma-delta modulator that outputs a larger number of bits can be used and the modulator can then be clocked at a lower rate. One skilled in the art will appreciate the number of bits used and the clock rate used are a function of the desired noise shaping and signal to noise ratio, and may be traded-off depending upon the requirements of a particular application.
One of the advantages of sigma-delta modulation of the time base is that the jitter or time variation produced on the sampling time (or sampling interval) due to the fact that digital filter 62 or decimator 21 (under control of sigma-delta modulator 20 or 66) respectively produces output samples at time intervals that may not correspond exactly to the specified sampling frequency (the 3.072 mHz clock rate in the illustrated embodiments) is varied by the sigma-delta modulator so that any noise that result from the error or jitter around the sampling point has a sigma-delta characteristic that can be removed by conventional filtering techniques, as for example, by filter 74.
FIG. 4 is a block diagram of an alternative system for determining frequency selection number 72. In FIG. 4, a memory 80 (which may be RAM or ROM, for example) is used to store a look up table containing twenty-bit numbers and the sampling frequency to which they correspond. In response to a frequency select signal from a user or an external source, decoder 82 selects the twenty-bit number from memory 80 most closely corresponding to the desired sampling frequency specified by the frequency select signal. The twenty-bit number is then output on bus 84 to sigma-delta modulator 66. The system of FIG. 4 can be used in conjunction with all embodiments of the invention.
The sample rate converted digital data stream on line 64 optionally is sent to filter 74 which operates in a manner analogous to filter 11 in FIG. 2. That is, depending on the performance requirements of the particular application, filter 74 may be used to filter out sigma-delta noise on the digital data stream on line 64 as a result of sigma-delta modulation control of sinc filter 62. In one embodiment of the invention, filter 74 may be a sinc-type filter, such as a sinc 964 -type filter. The filtered digital data stream having a data rate of 3.072 mHz on line 86 is then fed into circuit part 90 of circuit 100.
The filtered digital data stream on line 86 is then sent to interpolator 92. Interpolator 92 increases the sample rate of the digital data stream on line 86 by using a sample and hold technique or an interpolation technique under control of sigma-delta modulator 94. The use of a sample and hold technique is advantageous because it automatically compensates for the energy lost in creating the images of the original signal due to the interpolation process. One skilled in the art will appreciate that other techniques, such as interpolation techniques that insert zeroes between data samples may be used to increase the sample rate of the data stream on line 86. The higher rate digital data stream on line 96 is then sent to low-pass filter 98 that removes images and sigma-delta noise from the digital data stream on line 96 that may be present as a result of the interpolation process. In one embodiment, digital filter 98 is a sinc 963 -type filter. Filter 52 could, however, be any type of IIR or FIR filter.
The filtered digital data stream on line 102 is then sent to a decimation block 104 that decimates the digital data stream on line 102 by a fixed decimation ratio (96 in the illustrated embodiment). The decimated digital data stream on line 106 is then filtered by low pass filter 108 to remove images and sigma-delta noise as a result of the NONUNIFORM sampling. The filtered digital data stream on line 110 is then sent to a decimation block 112 that decimates the digital data stream on line 110 by a fixed decimation ratio (4 in the illustrated embodiment) to provide the digital data stream on line 114 at the data rate (Fs2) selected by a 20 bit sampling frequency selection number 116.
It is to be noted that the digital data streams on lines 86, 96, 102, 106, and 110 are indicated as being n-bits wide in FIG. 3. N may be any number of bits and is typically chosen to be the widest bit stream commensurate with the signal-to-noise ratio requirements of the particular application. Furthermore, the digital data streams may be different widths on each of the lines.
The n-th order m-bit sigma-delta modulator 94 provides a four-bit number on line 117 that controls interpolator 92 to produce the digital data stream on line 96. In one embodiment, sigma-delta modulator 94 is a third order four-bit modulator. Sigma-delta modulator 94 is also clocked using the 3.072 mHz clock 70.
In one embodiment, a twenty-bit frequency selection number 116 (representing Fs2) is input into sigma-delta modulator 94N. Frequency selection number 116 ranges from -219 to +219. This twenty-bit number controls the precision with which the four-bit number output by sigma-delta modulator 94 represents the desired sampling rate (Fs2) of the output digital data stream on line 114. Sigma delta modulator 94 modulates the twenty-bit number to produce sigma-delta modulated four-bit codes that control interpolator 92. The first bit of the code is a sign bit. The remaining three bits produce codes that control the interpolation ratio (i.e., the factor by which the sample rate of the digital data stream on line 86 is increased) provided by interpolator 92 to effectively convert the sample rate of the data stream.
Table 2 illustrates the relationship among the four-bit codes that are produced by sigma-delta modulator 94, the ratio by which the sample rate of the digital data stream on line 86 is increased, and the sampling frequency that the four-bit code corresponds to when modulator 94 is clocked using a 3.072 mHz clock. Some examples will illustrate the operation of this part of the system.
TABLE 2______________________________________     SAMPLE RATE     INCREASE FACTOR                   CORRESPONDING     ALLOW P CLOCKS                   TO SAMPLING4 BIT CODE     TO PASS THROUGH                   FREQUENCY OF (kHz)______________________________________+4        8             64+3        7             56+2        6             48+1        5             40 0        4             32-1        3             24-2        2             16-3        1              8-4        0             DC______________________________________
Assume, for purposes of illustration, that the sample rate of the digital data stream on line 86 is an oversampled data stream having a constant sample rate of 3.072 mHz as a result of the interpolation/decimation process performed by circuit part 51 on the digital data stream on line 50. Assume that the desired sample rate (Fs2) of the digital data stream on line 114 is 32 kHz. To produce the digital data stream on line 114 at 32 kHz, the digital data stream on line 110 must have a sample rate of 128 kHz and the digital data stream on line 96 must have a sample rate of 12.288 mHz. Therefore, twenty-bit frequency selection number 116 is selected such that upon sigma-delta modulation by the third order four-bit sigma-delta modulator 94, the four-bit codes generated will be, on average, a 0 code, although other four-bit codes will be produced but with a lower frequency of occurrence.
Interpolator 92 uses, in one embodiment, a sample and hold technique under control of sigma-delta modulator 94 to increase the sample rate of the digital data stream on line 86. The use of a sample and hold technique is advantageous because it automatically compensates for the energy lost in creating the images of the original signal due to the interpolation process.
A key point to remember is that the 0 code is the resulting average of all codes produced by sigma-delta modulator 94 upon sigma-delta modulation of twenty-bit frequency selection number 116. A 0 code is not produced every time sigma-delta modulator 94 is clocked even though the sample rate of the digital data stream on line 86 and the sample rate of the digital data stream on line 114 are related to each other by an integer multiple. Even if the sample rates were related to each other by an integer multiple, any errors, no matter how small, that result in a temporal displacement between the sample points in the digital data stream on line 86 and the sample points in the rate-converted digital data stream on line 96 would increase the signal-to-noise ratio to a point where the conversion process would not be acceptable. In the present invention, the time base (i.e., the temporal spacing between samples) is sigma-delta modulated so that the errors due to temporal displacement between the digital data stream on line 86 and the rate-converted digital data stream on line 96 that cause noise are pushed into a higher frequency range. This noise is then removed by conventional filtering techniques such as in digital filters 98 and 108.
As shown in Table 2, the 0 code (on average) directs interpolator 92 to increase the sample rate of the digital data stream on line 86 by a factor of four. Interpolator 92 uses, in one embodiment, a sample and hold technique under control of sigma-delta modulator 94 to increase the sample rate of the digital data stream on line 86. The use of a sample and hold technique is advantageous because it automatically compensates for the energy lost in creating the images of the original signal due to the interpolation process. Alternatively, interpolator 92 may increase the sample rate by interpolation using a zero fill technique to insert four zeros between every sample of the digital data stream on line 86. Inserting zeros into the digital data stream on line 86 will reduce the gain of the original signals because of dilution of the signal. The higher sample rate digital data stream on line 96 has a sample rate of, on average, 12.288 mHz in this example. Upon decimation by decimator circuit 104 and decimator circuit 112, the digital data stream on line 114 emerges with a sample rate of, on average, 32 kHz.
In another example, assume that the desired sample rate of the digital data stream on line 114 is 4 kHz. To produce the digital data stream on line 114 at 4 kHz, the digital data stream on line 110 must have a sample rate of 16 kHz and the digital data stream on line 96 must have a sample rate of 1.536 mHz. Therefore, 20-bit frequency selection number 116 is selected such that sigma-delta modulator 94 produces, on average, an equal number of -3 and -4 codes, although other 4-bit codes will be produced, but with a lower frequency of occurrence. As shown in Table 2, the -3 code directs interpolator 92 not to increase the sample rate (because the sample rate increase factor is 1). This corresponds to a sampling frequency of 8 kHz for the clock frequencies and interpolation ratios illustrated.
The -4 code controls interpolator 92 to increase the sample rate of the digital data stream by a factor of zero. That is, interpolator 92, in response to a -4 code, produces no output, thus effectively decimating the digital data stream on line 86.
At the illustrated interpolation ratios and clock frequencies, the -3 code represents a sampling frequency of 8 kHz and the -4 code represents a sampling frequency of DC (i.e., no signal). Therefore, on average of many samples, the -3 and -4 4-bit codes represent a sampling frequency of 4 kHz. Thus, on average of many samples, after decimation by decimator 104 and decimator 112, the data rate of the digital data on line 114 will be, on average, 4 kHz.
One skilled in the art will appreciate that any sampling frequencies within the 0 to 64 kHz range may be produced by varying the ratio of four-bit codes produced by sigma-delta modulator 94. For example, to obtain a sampling frequency between 56 kHz and 64 kHz, the appropriate ratio of +3 and +4 codes would be output by sigma-delta modulator 94 as a function of twenty-bit number 116. One skilled in the art will also appreciate that any sample rate within the working range of the system can be produced through the appropriate combination of four-bit codes.
As previously discussed with respect to circuit part 51, one of the advantages of sigma-delta modulation of the time base in circuit part 90 is that the jitter or time variation produced on the sampling time (or sampling interval) due to the fact that interpolator 92 (under control of sigma-delta modulator 94) produces output samples at time intervals that may not correspond exactly to the specified output sampling frequency (0 kHz to 64 kHz in the illustrated embodiment) on line 117 is varied by the sigma-delta modulator so that any noise that results from the error or jitter around the sampling point has a sigma-delta characteristic that can be removed by conventional filtering techniques, as for example, by filter 98.
The alternative system for determining a frequency selection number as illustrated in FIG. 4 can also be used to determine 20 bit frequency selection number 116 in the same manner.
FIG. 5 illustrates another embodiment of the invention in which digital phase locked loops 120 and 122 are incorporated into the circuits of FIGS. 2 or 3. The phase locked loops allow the digital-to-digital converter to operate at and lock to external clock signals, such as off-chip signals. Phase locked loop 120 locks to and tracks an external frequency source on line 124. The frequency source on line 124 may be the sampling frequency select signal or the twenty bit frequency selection number illustrated in FIGS. 2 and 3, respectively. The frequency source on line 124 may be a clock running at the data rate (Fs1) of the digital data coming into the circuit on line 126. Alternatively, the frequency source on line 124 may be a clock from the circuit that supplies the digital data on line 126 at a data rate of Fs1. Therefore, phase locked loop 120 will track changes in the clock that controls the data rate of the digital data on line 126, thus allowing this part of the circuit to respond to an external frequency source. In this way, the first part of circuit 150 including interpolator 128, filter 130, and decimator 132 can be made to track the clock that controls the data rate of the digital data on line 126, thus allowing this part of the circuit to operate independent of the clock rate of clock 134. In a like manner, phase locked loop 122 responds to an external frequency source on line 136 to control interpolator 138, filter 140, and decimator 142. The frequency source on line 136 may be the sampling frequency select signal or the twenty bit frequency selection number illustrated in FIG. 2 and 3, respectively. The external frequency source on line 136 is typically a clock running at the desired output data rate (Fs2) of the digital data on line 144. In this manner, the data rate of the digital data on line 144 can be made to be independent of the clock rate of clock 134, since the phase locked loop 122 locks to and tracks the frequency of the external frequency source on line 136.
FIG. 5A illustrates another embodiment of the invention in which phase locked loop 120 receives, on line 124, an external frequency source having a frequency equal to the clock rate of the digital data stream being supplied to interpolator 128. Since phase locked loop 120 responds to a clock having the data rate of the incoming digital data stream, any changes in the frequency of the digital data on line 126 are tracked by phase locked loop 120, thereby keeping the operation of interpolator 128, filter 130, and decimator 132 in synchronism with the data rate of the incoming digital data on line 126. The circuit of FIG. 5A also includes the sigma-delta modulator and variable interpolation/fixed decimation circuitry 90 illustrated in FIG. 3. This portion of the circuitry of FIG. 5A operates in the manner described in conjunction with FIG. 3. The circuit of FIG. 5A is advantageous in that the fixed interpolation, variable decimation portion can be locked to the data rate of the incoming digital data stream. The data rate of the outgoing digital data stream on line 114 is controlled by the 20 bit frequency selection number 116. Thus, both portions 146 and 90 can respectively receive data and output data independent of the clock rate of clock 134. In addition, the data rate of the digital data on line 114 can be independent of and unrelated to the data rate of the digital data on line 126. These same advantages also are provided by the circuit of FIG. 5. One skilled in the art will appreciate that FIGS. 5 and 5A are exemplary and that phase locked loops and sigma-delta modulators can be combined in other ways in accordance with the present invention.
FIG. 6 illustrates a detailed embodiment of phase locked loop 120 of FIG. 5. Digital phase locked loop 120 incorporates a sigma-delta modulator such as sigma-delta modulator 20 or 66.
In circuit 120, an external clock source on line 124 is applied to a frequency counter 164 that produces a signal representative of the period of the external frequency source on line 124. In addition, the external clock on line 124 is applied to a phase detector 166 that produces a signal proportional to the phase difference between the external clock on line 124 and a signal on line 168 to be described in more detail hereinafter. The output of the phase detector 166 is filtered by differentiating filter 170 and summed in summer 172 with the signal representative of the period of the external clock source on line 124 from the frequency counter 164. The output of summer 172 is fed into an integrating filter 174 that functions as a low-pass filter. The output of integrating filter 174 is then sent to a circuit 176 that converts the period to a frequency by performing a 1/period function and providing any application dependent scaling of the frequency signal. The signal from circuit 176 is then sent to sigma-delta modulator 66. The four-bit code from sigma-delta modulator 66 is used to control decimator 132 or decimate block 21 or sinc filter 62 in the same manner as described in connection with the embodiment of FIGS. 2 and 3, respectively.
The four-bit code is also fed into a clock generation circuit 178 that effectively produces an output clock at 384 times greater than the signal on line 124. Circuit 178 performs this function by suppressing a certain number of 24.576 mHz clock cycles in response to the four-bit code from sigma-delta modulator 66. The following examples will serve to illustrate. Assume sigma-delta modulator 66 is clocked by a 3.073 mHz clock. For every 3.072 mHz clock, there are eight 24.576 mHz clocks applied to circuit 178. In accordance with Table 1, circuit 178 suppresses a number of 24.576 mHz clocks as a function of the four bit code output by sigma-delta modulator 66. For example, if the external frequency source on line 162 is 48 kHz, then sigma-delta modulator 66 outputs, on average, a +2 code. The +2 code directs circuit 178 to allow six out of every eight 24.576 mHz clocks to pass through. Stated another way, circuit 178 suppresses two out of every eight 24.576 mHz clocks in response to a +2 code.
If the external clock frequency source is 4 kHz, then sigma-delta modulator 66 outputs, on average, an equal number of -3 and -4 codes. The -3 code directs circuit 178 to allow one out of every eight 24.576 mHz clocks to pass through (i.e., circuit 178 suppresses seven out of every eight 24.576 mHz clocks in response to a -3 code). The -4 code directs circuit 178 to allow no 24.576 mHz clocks to pass through (i.e., circuit 178 suppresses eight out of every eight 24.576 mHz clocks in response to a -4 code). On average, therefore, one out of every sixteen 24.576 mHz clocks will pass through suppressor circuit 178 in response to an average of -3 and -4 codes.
If, however, the same clocks are suppressed for each four-bit code from sigma-delta modulator 66, then unwanted tones may appear in the output data stream on line 182. Therefore, circuit 178 also performs the additional function of randomly suppressing clock cycles in order to prevent unwanted tones in the output data stream on line 182. Randomizing ensures that pulses in each of the eight positions (recall that there are eight 24.576 mHz clock pulses for each 3.072 mHz clock pulse controlling sigma-delta modulator 66) are suppressed equally, on average. This may be accomplished by providing a latch for each bit position that is set whenever the pulse in that position is suppressed. Pulses in that position are not suppressed again until all latches corresponding to all the positions have been set, at which time the latches are cleared and the sequence of suppression is repeated. This reduces tones that result from the clock pulse suppressor. Clock suppressor circuits are well-known in the art. One example of such a circuit may be found in Phase Locked Loops, Theory, Design, and Applications by Dr. Roland E. Best, published by McGraw-Hill Book Company, ©1984. Clock randomizer/suppressor circuit 178 outputs a clock signal on line 182 that is sent through divider 184 having a divider ratio of 96 and a divider 188 having a divider ratio of 4 that reduce the suppressed and randomized 24.576 mHz clock output by clock randomizer circuit 178 to the frequency of the external clock on line 124. Circuits 184 and 188 may be counters.
For the examples just discussed above, if the external clock on line 124 is 48 kHz, then the signal on line 182 is approximately 18.432 mHz. When divided by ninety-six and then four, the signal on line 168 is 48 kHz. If the external clock on line 124 is 4 kHz, then the signal on line 182 is approximately 1.536 mHz. When divided by ninety-six and then four, the signal on line 168 is 4 kHz.
Circuit 176, sigma-delta modulator 66 and clock randomizer/suppressor circuit 178 together form a digitally-controlled oscillator.
FIG. 7 illustrates one embodiment of the phase locked loop 122 used in the circuit of FIG. 5. Phase locked loop 122 is the same as phase locked loop 120.
In circuit 122, an external clock source on line 136 is applied to a frequency counter 164 that produces a signal representative of the period of external frequency source on line 136. In addition, the external clock on line 136 is applied to phase detector 166 that produces a signal proportional to the phase difference between the external clock on line 136 and a signal on line 166 to be described in more detail hereinafter. The output of phase detector 166 is filtered by differentiating filter 170 and summed in summer 172 with the signal representative of the period of the external clock source on line 136 from the frequency counter 164. The output of summer 172 is fed into an integrating filter 174 that functions as a low-pass filter. The output of integrating filter 174 is then sent to a circuit 176 that converts the period to a frequency by performing a 1/period function and providing any appropriate scaling. The signal from circuit 136 is then sent to sigma-delta modulator 94. The four-bit code from sigma-delta modulator 94 is used to control interpolator 138 or interpolators 30 or 92 in the same manner as described in connection with the embodiment of FIGS. 2 and 3, respectively.
The 4-bit code is also fed into a clock generation circuit 179 that effectively produces an output clock at 384 times greater than the signal on line 136. Circuit 179 performs this function by suppressing a certain number of 24.576 mHz clock cycles in response to the 4-bit code from sigma-delta modulator 94. The following examples will serve to illustrate. Assume sigma-delta modulator 94 is clocked by a 3.072 mHz clock. For every 3.072 mHz clock, there are eight 24.576 mHz clocks applied to circuit 179. In accordance with Table 2, circuit 179 suppresses a number of 24.576 mHz clocks as a function of the 4-bit code output by sigma-delta modulator 94. For example, if the external frequency source on line 136 is 32 kHz, then sigma-delta modulator 94 outputs, on average, a 0 code. The 0 code directs circuit 179 to allow four out of every eight 24.576 mHz clocks to pass through. Stated another way, circuit 179 suppresses four out of every eight 24.576 mHz clocks in response to a 0 code.
If the external clock frequency source is 4 kHz, then sigma-delta modulator 94 outputs, on average, an equal number of -3 and -4 codes. The -3 code directs circuit 179 to allow one out of every eight 24.576 mHz clocks to pass through (i.e, circuit 179 suppresses seven out of every eight 24.576 mHz clocks in response to a -3 code). The -4 code directs circuit 179 to allow no 24.576 mHz clocks to pass through (i.e., circuit 179 suppresses eight out of every eight 24.576 mHz clocks in response to a -4 code). On average, therefore, one out of every sixteen 24.576 mHz clocks will pass through suppressor circuit 178 in response to an average of -3 and -4 codes.
The remainder of phase locked loop 122 including randomizer/suppressor circuit 179, divider 184, and divider 188 operate in the same manner as discussed in connection with phase locked loop 120.
For the examples just discussed above, if the external clock on line 136 is 32 kHz, then the signal on line 182 is approximately 12.288 mHz. When decimated by ninety-six and then four, the signal on line 168 is 23 kHz. If the external clock on line 136 is 4 kHz, then the signal on line 182 is approximately 1.536 mHz. When decimated by ninety-six and then four, the signal on line 168 is 4 kHz.
Circuit 176, sigma-delta modulator 94, and clock randomizer/suppressor circuit 179 together form a digitally-controlled oscillator.
The embodiments of the present invention including phase locked loops allow the digital-to-digital converter to accept digital data at any data rate within the working range of the system, and lock to an externally supplied clock source that allows conversion of the incoming digital data to a data rate that is not necessarily the same as or even an integer or rational relationship with the master clock controlling the digital-to-digital converter.
The embodiments of the invention illustrated in FIGS. 2-3 and 5-5A may be characterized as using a combination of fixed interpolation followed by variable decimation and then variable interpolation followed by fixed decimation. That is, with reference to FIG. 2, the digital data stream on line 12 is interpolated by a fixed ratio to increase the sample rate. This higher sample rate digital signal is then variably decimated under control of sigma-delta modulator 20 to provide the digital data stream on line 14 at another sample rate. Thereafter, the digital data stream on line 28 (which has the same data rate as the digital data stream on line 14) is variably interpolated under control of sigma-delta modulator 32 to variably increase the sample rate. This higher sample rate digital signal is then decimated by a fixed ratio to provide the digital data stream on line 42 at another sample rate. The sample rates of the digital data stream on lines 14 and 28 are at a common sample rate. In the illustrated embodiment, the common sample rate is 3.072 mHz.
Reference is now made to FIG. 8 which is a flow chart illustrating a first embodiment of a method of the present invention. FIG. 8 illustrates the method of fixed interpolation followed by variable decimation and then variable interpolation followed by fixed decimation.
In FIG. 8, the method begins in step 200 in which the input digital data having a first data rate is received. From step 200, the method proceeds to step 202 in which the input digital data is interpolated by a fixed ratio to increase the sample rate of the digital data to provide an oversampled digital data stream. From step 202, the method proceeds to step 204 in which a first sampling frequency select signal representative of the sample rate of the digital data received in step 200 is received. From step 204, the method proceeds to step 206 in which the first sampling frequency select signal is sigma-delta modulated. From step 206, the method proceeds to step 208 in which the interpolated digital data is decimated under control of the sigma-delta modulated frequency select signal by a ratio determined by the sigma-delta modulated first sampling frequency select signal. From step 208, the method proceeds to step 210 in which a second sampling frequency select signal representative of the desired output sample rate is received. From step 210, the method proceeds to step 212 in which the second sampling frequency select signal is sigma-delta modulated. From step 212, the method proceeds to step 214 in which the digital data is interpolated by a ratio determined by the sigma-delta modulated second sampling frequency select signal to increase the sample rate of the digital data. From step 214, the method proceeds to step 216 in which the interpolated digital data is decimated to provide the output digital data at the desired sample rate. From step 216, the method proceeds to step 218 in which the digital signal is output.
FIG. 9 is a block diagram broadly illustrating a second embodiment of the invention. As with the first embodiment illustrated in FIGS. 2-3, the overall purpose of circuit 250 is to receive a digital data stream on line 12 at any data rate within a predetermined working range of the system and to convert the digital data to a digital data stream on line 42. The data rate of the digital data stream on line 42 can be the same as, higher, or lower than the data rate of the digital data stream on line 12.
Except as specified, circuit 250 operates in the same manner as the first embodiment of the invention.
In circuit part 274 of the circuit 250 illustrated in FIG. 9, the digital data on line 12 is interpolated by interpolator 252 under control of clock randomizer/suppressor circuit 178 which is in turn controlled by sigma-delta modulator 20 to produce a higher sample rate digital signal on line 17. Interpolator 252 increases the sample rate of the digital data stream (that is, converts the digital data stream into a higher sample rate digital data stream) on line 17 by using a sample and hold technique that repeats the digital sample for a specified number of clock cycles in a manner well-known to those skilled in the art. One skilled in the art will appreciate that other techniques may be used for increasing the sample rate of the data stream on line 12, such as interpolation techniques that insert zeros between data samples. The purpose of interpolator 252 is to increase the sample rate of the digital data stream on line 12 to create a so-called oversampled signal.
The interpolation ratio (i.e., the ratio by which the sample rate of the digital data on line 12 is increased by interpolator 252 is controlled by clock randomizer/suppressor circuit 178 which is in turn controlled by sigma-delta modulator 20.
The higher sample rate digital data stream on line 17 is then sent to a digital filter 18 which removes any images of the original digital signal as a result of the interpolation process. The filtered digital data stream on line 19 is then sent to a decimation block 254 that decimates the digital data stream on line 19 by a fixed decimation ratio to produce the digital data stream on line 14 having a fixed predetermined data rate. Although filter 18 and decimation block 254 have been illustrated as separate circuit elements for illustrative purposes, one skilled in the art will appreciate that these functions may be performed by a single computation element, such as an FIR or IIR filter in a well known manner. Sigma-delta modulator 20 operates in the same manner as described in connection with the embodiment of FIGS. 2-3.
The m-bit code output signal on line 260 from sigma-delta modulator 20 is fed into the clock randomizer/suppressor circuit 178 that effectively produces an output clock at 384 times greater than the data rate of the digital signal on line 12. In one embodiment, clock 262 is a 24.576 mHz clock. Circuit 178 operates in the same manner as already described in connection with FIGS. 6 and 7. The following explanation is provided for additional clarification.
Circuit 178 provides a clock on line 258 by suppressing a certain number of clocks from clock 262 in response to the m-bit code on line 260 from sigma-delta modulator 20. If, however, clocks in the same temporal positions are suppressed for each multi-bit code from sigma-delta modulator 20, then unwanted tones may appear in the output data stream on line 258. Therefore, circuit 178 also performs the additional function of randomly suppressing clock cycles in order to prevent unwanted tones in the output data stream on line 258. As described previously, clock suppressor and randomizer circuits are well known in the art. One example of such a circuit may be found in Phase Locked Loops by Dr. Roland E. Best, published by McGraw-Hill Book Company, copyright 1984. Clock randomizer/suppressor circuit 178 is needed in the second embodiment to produce a clock on line 258 having a clock frequency that is 384 times the data rate specified by sampling frequency selection signal 24 since sigma-delta modulator 20 is clocked using a fixed clock frequency and a variable clock frequency is needed to variably interpolate the data on line 12. Clock randomizer/suppressor circuit 178 outputs a clock signal on line 258 that controls the interpolation of interpolator 252.
The digital data at the predetermined data rate on line 14 is optionally filtered by a filter 11 as described in connection with the first embodiment of the invention. The filter data from filter 11 on line 28 is sent to circuit part 276 of circuit 250.
In circuit part 276 of the circuit 250 illustrated in FIG. 9, the filtered digital data stream on line 28 is sent to interpolator 270. Interpolator 270 increases the sample rate of the digital data stream (that is, converts the digital data stream into a higher sample rate digital data stream) on line 28 by, for example, inserting zeros between data samples, in a manner well-known to those skilled in the art. One skilled in the art will appreciate that other techniques may be used for increasing the sample rate of the data stream on line 28, such as sample and hold techniques. As noted previously, the purpose of interpolator 170 is to increase the sample rate of the digital data stream on line 28 to create a so-called oversampled signal.
A higher sample rate digital data stream on line 34 is then sent to a digital filter 36 which removes any images of the original digital signal as a result of the interpolation process. The filtered digital data stream on line 38 is then sent to a decimation block 272 that decimates the digital data stream on line 38 under control of clock randomizer/suppressor circuit 179 which is in turn controlled by the sigma-delta modulator 32 as will be explained in more detail hereinafter. Although filter 36 and decimation block 272 have been illustrated as separate circuit elements for illustrative purposes, one skilled in the art will appreciate that these functions may be performed by a single computational element, such as an FIR or IIR filter in a well-known manner. Sigma-delta modulator 20 operates in the same manner as described in connection with the embodiment of FIGS. 2-3.
The m-bit code output signal on line 264 from sigma-delta modulator 32 is fed into a clock randomizer/suppressor circuit 179 that effectively produces an output clock at 384 times greater than the data rate of the digital signal on line 28. In one embodiment, clock 262 is a 24.576 mHz clock. Circuit 179 operates in the same manner as circuit 178. The following explanation is provided for additional clarification.
Circuit 179 provides a clock on line 268 by suppressing a certain number of cycles of clocks from clock 262 in response to the m-bit code on line 264 from sigma-delta modulator 32. If, however, the same clocks in the same temporal positions are suppressed for each multi-bit code from sigma-delta modulator 32, then unwanted tones may appear in the output data stream on line 268. Therefore, circuit 179 also performs the additional function of randomly suppressing clock cycles in order to prevent unwanted tones in the output data stream on line 268. As described previously, clock suppressor and randomizer circuits are well-known in the art. One example of such a circuit may be found in Phase Locked Loops by Dr. Roland E. Best, published by McGraw-Hill Book Company, ©1984. Clock suppressor/randomizer circuit 179 is needed in the second embodiment to produce a clock on line 268 having a clock frequency that is 384 times the data rate specified by sampling frequency selection number 44 since sigma-delta modulator 32 is clocked using a fixed clock frequency and a variable clock frequency is needed to variably decimate the data on line 38. Clock randomizer/suppressor circuit 179 outputs a clock signal on line 268 that controls the decimation of decimator 272 to provide the digital data stream on line 42 having a sample rate (Fs2) selected by sampling frequency select signal 44.
FIG. 10 illustrates a more detailed embodiment 300 of the circuit illustrated in FIG. 9. The purpose and operation of circuit 300 is analogous to the first embodiment of the invention illustrated in FIGS. 2-3.
The higher sample rate digital data on line 60 is then sent to a sinc 963 -type filter 302 that removes images of the digital data stream on line 60 that result from the interpolation process. The filtered higher sample rate digital data on line 304 is then sent to interpolator 306 that increases the sample rate by a variable ratio so that the digital data on line 308, after filtering by filter 310 and decimation by a fixed ratio of eight in decimator 314, emerges on line 64 with a sample rate of 3.072 mHz. Filter 310 may be an FIR or IIR filter. The functions of decimator 314 and filter 74 may be combined into a single element as noted previously.
Sigma-delta modulator 66 produces a four-bit code representative of frequency selection number 72 at a constant rate of 3.072 mHz in response to clock 70. However, interpolator 306 must produce the digital data stream on line 308 having a sample rate of 24.576 mHz so that, when decimated by a factor of eight by decimator 314, the data emerges on line 64 with a sample rate of 3.072 mHz. Therefore, clock randomizer/suppressor circuit 178 is needed to produce a variable rate clock on line 316 to variably interpolate the data on line 304.
Table 1 illustrates the relationship among the four-bit codes that are produced by sigma-delta modulator 66, the number of clocks that are allowed to pass through randomizer/suppressor circuit 178 and the output sample rate that the four-bit code corresponds to when modulator 66 is clocked using a 3.072 mHz clock and when clock randomizer/suppressor circuit 178 and interpolator 306 are clocked using a 24.576 mHz clock. Some examples will illustrate the operation of the second embodiment.
Assume, for purposes of illustration, that the sample rate of the digital data stream on line 50 is 48 kHz. Interpolator 52 increases this sample rate to 192 kHz. Interpolator 58 increases the 192 kHz signal to 18.432 mHz. Twenty-bit frequency selection number 72 is selected such that upon sigma-delta modulation by the fourth order four-bit sigma-delta modulator 66, the four-bit codes generated will be, on average, a +2 code although other four-bit codes will be produced with a lower frequency of occurrence. In accordance with Table 1, the +2 code is processed by clock randomizer/suppressor circuit 178 to allow six out of every eight 24.576 mHz clock cycles from clock 262 to pass through to generate a clock having an average frequency of 18.432 mHz. Interpolator 306 delivers data on line 308 at a rate of 24.576 mHz. Data arrives at the interpolator 306 on line 304 at 18.432 mHz in this example. Each time the 18.432 mHz clock on line 316 is active, a new data point has arrived at the interpolator input on line 304. Interpolator 306 inserts this data point into the outgoing data stream on line 308 so that the 18.432 mHz data is delivered at 24.576 mHz on line 308. Interpolator 306 performs this function by sample and holding each 18.432 mHz data point every 24.576 mHz clock until the next 18.432 mHz data point arrives. Alternatively, Interpolator 306 may insert zeros between each data point at 18.432 mHz to deliver the data at 24.576 mHz. The use of a sample and hold technique is advantageous because it automatically compensates for the energy lost in creating the images of the original signal due to the interpolation process. As a result, interpolator 306 increases the sample rate of the digital data stream on line 304 from 18.432 mHz to 24.576 mHz on line 308. Upon filtering by filter 310 and decimation by decimator 314, the digital data emerges on line 64 with a sample rate of, on average, 3.072 mHz.
In another example, assume that the digital data stream on line 50 has a data rate of 4 kHz. Interpolator 52 increases this data rate to 16 kHz. Interpolator 58 increases the 16 kHz data rate to 1.536 mHz. In order that the digital data stream on line 64 have a data rate of 3.072 mHz, the digital data stream on line 60 at 1.536 mHz must be effectively interpolated by a factor of sixteen so that the data rate of the digital data stream on line 308 has a data rate of 24.576 mHz. Therefore, the twenty-bit frequency selection number 72 is chosen such that sigma-delta modulator 66 produces, on average, an equal number of -3 and -4 codes although other four-bit codes will be produced, but with a lower frequency of occurrence. That is, occasionally, -2, -1, and even less frequently, +1, +2 codes will be produced. As shown in Table 1, the -3 code directs circuit 178 to allow one out of every eight 24.576 mHz clocks to pass through (i.e. circuit 178 suppresses seven out of every eight 24.576 mHz clocks in response to a -3 code). The -4 code directs circuit 178 to allow no 24.576 mHz clocks to pass through (i.e. circuit 178 suppresses eight out of every eight 24.576 mHz clocks in response to a -4 code). On average, therefore, one out of every sixteen 24.576 mHz clocks will pass through suppressor circuit 178 in response to an average of -3 and -4 codes.
At the illustrated interpolation ratios and clock frequencies, the -3 code represents a sampling frequency of 8 kHz and the -4 code represents a sampling frequency of DC (i.e. no signal). Therefore, on average of many samples the -3 and -4 four-bit codes represent a sampling frequency of 4 kHz times 384 to provide a clock on line 316 at (384) (4 kHz)=1.536mHz. In the manner just described in the previous example, interpolator 306 responds to the clock on line 316 to increase the sampling frequency of the 1.536 mHz data on line 304 to 24.576 mHz on line 308.
It is to be noted that the digital data streams are indicated as being N-bits wide. N may be any number of bits and is typically chosen to be the widest bit stream commensurate with the signal-to-noise ratio requirements of the particular application.
The sample rate converted digital data stream on line 64 optionally is sent to filter 74 which operates as described in connection with FIG. 3. The filtered digital data stream having a data rate of 3.072 mHz on line 86 is then fed into circuit part 303 of circuit 300.
The filtered digital data stream on line 86 is then sent to interpolator 320. Interpolator 320 increases the sample rate of the digital data stream on line 86 by a factor of eight using, for example, a zero fill technique that inserts zeros between the digital samples. As is well-known, the parameters of filter 324 can be adjusted to compensate for any loss of gain. A higher sample rate signal on line 322 output by interpolator 320 (now at 24.576 mHz) is then fed into digital filter 324.
As stated previously, other techniques, such as sample and hold techniques, may be used to increase the sampling rate in place of interpolator 320.
The filtered higher sample rate digital data on line 326 is then sent to decimator 328 that decreases the sample rate by a variable ratio so that the digital data on line 114, after filtering by filter 98 and decimation by a fixed ratio of ninety-six in decimator 104 and a fixed ratio of four in decimator 112, emerges on line 114 with a sample rate specified by frequency selection number 116. Filter 98 is a sinc 933 -type filter but could be any type of FIR or IIR filter. In addition, filter 98 and decimator 328 could be combined into a single element as noted previously.
Sigma-delta modulator 94 produces a four-bit code representative of frequency selection number 116 at a constant rate of 3.072 mHz in response to clock 70. However, decimator 328 must produce the digital data stream on line 96 having sample rates of, for example, between 1.536 mHz and 24.576 mHz depending upon the desired sample rate of the output data stream. Therefore, clock randomizer/suppressor circuit 179 is needed to produce a variable rate clock on line 318 to variable decimate the data on line 326.
Table 2 illustrates the relationship among the four-bit codes that are produced by sigma-delta modulator 94, the number of clocks that are allowed to pass through randomizer/suppressor circuit 179, and the output sample rate that the four-bit code corresponds to when modulator 94 is clocked using a 3.072 mHz clock and when clock randomizer/suppressor circuit 179 is clocked using a 24.576 mHz clock. Some examples will illustrate the operation of the second embodiment.
Assume, for purposes of illustration, that the sample rate of the digital data stream on line 86 is an oversampled data stream having a constant sample rate of 3.072 mHz. Assume that the desired sample rate of the digital data stream on line 114 is 48 kHz. Interpolator 320 increases the data rate of the digital data stream on line 86 by a factor of eight to 24.576 mHz. To produce the digital data stream on line 114 at 48 kHz, the digital data stream on line 102 must have a sample rate of 192 kHz and the digital data stream on line 110 must have a sample rate 18.432 mHz. Therefore, twenty-bit frequency selection number 116 is selected such that upon sigma-delta modulation by the fourth order four-bit sigma-delta modulator 94, the four bit codes generated will be, on average, a +2 code although other four bit codes will be produced but with a lower frequency of occurrence.
The +2 code is then applied to clock randomizer/suppressor circuit 179. For every 3.072 mHz clock applied to sigma-delta modulator 94, there are eight 24.576 mHz clocks applied to clock randomizer/suppressor circuit 179. In accordance with Table 2, circuit 179 suppresses a number of 24.576 mHz clocks as a function of the four-bit code output by sigma-delta modulator 94. The +2 code directs circuit 98 to allow six out of every eight 24.576 mHz clocks to pass through. Stated another way, circuit 179 suppresses two out of every eight 24.576 mHz clocks in response to a +2 code. As discussed previously, circuit 179 randomly suppresses the specified number of clock cycles in order to prevent unwanted tones in the output data stream on line 318.
In another example, assume that the desired sample rate of the digital data stream on line 114 is 4 kHz. Interpolator 320 increases the data rate of the digital data stream on line 86 by a factor of eight to 24.576 mHz. To produce the digital data stream on line 114 at 4 kHz, the digital data stream on line 102 must have a sample rate of 16 kHz and the digital data stream on line 110 must have a sample rate of 1.536 mHz. Therefore, twenty-bit frequency selection number 116 is selected such that sigma-delta modulator 94 produces, on average, an equal number of -3 and -4 codes although other four-bit codes will be produced, but with a lower frequency of occurrence. That is, occasionally, -2, -1, and even less frequently, +1, +2 codes will be produced. As shown in Table 2, the -3 code directs circuit 179 to allow one out of every eight 24.576 mHz clocks to pass through (i.e., circuit 179 suppresses seven out of every eight 24.576 mHz clocks in response to a -3 code). The -4 code directs circuit 179 to allow no 24.576 mHz clocks to pass through (i.e., circuit 179 suppresses eight out of every eight 24.576 mHz clocks in response to a -4 code). On average, therefore, one out of every sixteen 24.576 mHz clocks will pass through suppressor circuit 179 in response to an average of -3 and -4 codes.
At the illustrated interpolation ratios and clock frequencies, the -3 code represents a sampling frequency of 8 kHz and the -4 code represents a sampling frequency of DC (i.e., no signal). Therefore, on average of many samples, the -3 and -4 four-bit codes represent a sampling frequency of 4 kHz times 384 to provide a clock on line 318 at (4 kHz (384)=1.536 mHz.
It is to be noted that digital data streams are indicated as being N-bits wide. N may be any number of bits and is typically chosen to be the widest bit stream commensurate with the signal-to-noise ratio requirements of the particular application.
The embodiments of the invention illustrated in FIGS. 9-10 may be characterized as using a combination of variable interpolation followed by fixed decimation and then fixed interpolation followed by variable decimation. That is, with reference to FIG. 9, the digital data stream on line 12 is interpolated under control of sigma-delta modulator 20 to provide the digital data stream on line 17 at a higher sample rate. This higher sample rate digital data stream is then decimated by a fixed ratio to provide the digital data stream on line 14 at another sample rate. Thereafter, the digital data stream on line 28 (which has the same data rate as the digital data stream on line 14) is interpolated by a fixed ratio to increase the sample rate. This higher sample rate digital signal is then variably decimated under control of sigma-delta modulator 32 to provide the digital data stream on line 42 at another data rate. The sample rates of the digital data stream on lines 14 and 28 are at a common sample rate. In the illustrated embodiment, the common sample rate is 3.072 mHz.
Reference is now made to FIG. 11 which is a flow chart illustrating a second embodiment of a method of the present invention. FIG. 11 illustrates the method of variable interpolation followed by fixed decimation and then fixed interpolation followed by variable decimation.
In FIG. 11, the method begins in step 340 in which the input digital data having a first data rate is received. From step 340, the method proceeds to step 342 in which a first sampling frequency select signal representative of the sample rate of the digital data received in step 340 is received. From step 340, the method proceeds to step 344 in which the first sampling frequency select signal is sigma-delta modulated. From step 344, the method proceeds to step 346 in which the digital data is interpolated by a ratio determined by the sigma-delta modulated first sampling frequency select signal to increase the sample rate of the digital data. From step 346, the method proceeds to step 348 in which the interpolated digital data is decimated by a fixed ratio. From step 348 the method proceeds to step 350 in which the decimated digital data from step 348 is interpolated by a fixed ratio to increase the sample rate of the digital data to provide an oversampled digital data stream. From step 350, the method proceeds to step 352 in which a second sampling frequency select signal representative of the desired output sample rate is received. From step 352, the method proceeds to step 354 in which the second sampling frequency select signal is sigma-delta modulated. From 354, the method proceeds to step 356 in which the interpolated digital data is decimated under control of the sigma-delta modulated frequency select signal by a ratio determined by the sigma-delta modulated second sampling frequency select signal to provide the output digital data at the desired sample rate. From step 356, the method proceeds to step 358 in which the digital signal is output.
Reference is now made to FIG. 12 which figure illustrates a third embodiment 370 of the present invention. In particular, FIG. 12 modifies the circuit of FIG. 10 by eliminating the clock randomizer/suppressor circuit. In all other respects, the components and operation of the circuit of FIG. 12 are the same as those illustrated in FIG. 10. The circuit of FIG. 12 operates in accordance with the method illustrated in FIG. 11.
Since the clock randomizer/suppressor circuit is eliminated, sigma-delta modulator 94 produces a four-bit code that directly controls the decimation ratio provided by decimation block 328 and sigma-delta modulator 66 produces a four-bit code that directly controls the interpolation ratio provided by interpolator 306.
Table 3 illustrates the relationship among the four-bit codes that are produced by sigma-delta modulator 66 or 94, the intervals at which decimator 328 produces an output or the ratio by which the sample rate on line 304 is increased, and the sampling frequency that the four-bit code corresponds to when modulator 66 or 94 is clocked using a 3.072 mHz clock. For example, a -4 code controls decimator 328 to produce one output for every sample on line 326 and a +3 code controls decimator 328 to produce one output every eight samples on line 326. In the same way, a -4 code controls interpolator 306 to maintain the same sample rate as on line 304 and a +3 code controls interpolator 306 to increase the sample rate on line 304 by a factor of eight.
TABLE 3______________________________________    SAMPLE RATE    INCREASE FACTOR CORRESPONDING    PRODUCE AN OUTPUT                    TO SAMPLING4 BIT CODE    EVERY P SAMPLES FREQUENCY OF (kHz)______________________________________+5       10              4.8+4       9               5.333+3       8               6+2       7               6.857+1       6               8 0       5               9.6-1       4               12-2       3               16-3       2               24-4       1               48-5       0               &#8734;______________________________________
FIG. 13 graphically illustrates the 1/n relationship between the four-bit codes and the corresponding sampling frequency. One skilled in the art will appreciate that the system is nonlinear in the sense of mapping the four-bit codes to a corresponding sampling frequency only because of the particular interpolation ratios, decimation ratios, and data rates chosen. However, the system itself is linear and, by providing an operation that corrects for the nonlinear mapping of the four-bit codes to the corresponding sampling frequency, a linearly mapped system as in the first two embodiments previously described can be provided. Alternatively, the interpolation ratios, decimation ratios, and data rates may be selected so that there is a linear relationship between four-bit codes and corresponding sampling frequencies. One skilled in the art will also appreciate that the 1/n relationship between four-bit codes and sampling frequency illustrated in FIG. 13 and Table 2 is meant to be exemplary only; other relationships are possible (for all embodiments of the invention) and are to be considered within the scope of the present invention.
The circuit illustrated in FIG. 12 can generate sampling frequencies within the 0 to 64 kHz range by varying the ratio of four-bit codes in the same manner as discussed in conjunction with the first two embodiments. The embodiment illustrated in FIG. 12 can also be used with the circuits illustrated in FIGS. 14 and 15 in the same manner.
Although the mapping between four-bit codes and sampling frequency is nonlinear in the embodiment illustrated in FIG. 12, this embodiment does provide certain advantages. In the embodiment illustrated in FIGS. 9-10, a clock randomizer/suppressor circuit was used. The clock randomizer/suppressor circuit can result in a system having a reduced signal to noise ratio as compared to the embodiments of the invention illustrated in FIGS. 2-3, since the clock randomizer/suppressor circuit reprocesses the sigma-delta modulated clock signal generated by the sigma-delta modulator and suppresses clock signals in a linear manner. This may degrade the noise shaping provided by the sigma-delta modulator. The circuit illustrated in FIG. 12 is advantageous in that the clock randomizer/suppressor circuit is eliminated thereby avoiding degradation in the signal to noise ratio.
FIG. 14 illustrates another embodiment 251 of the invention in which digital phase locked loops 120 and 122 are incorporated into the circuits of FIGS. 9 or 10. The phase locked loops operate as previously described in connection with the discussion of FIG. 5.
FIG. 15 illustrates another embodiment 253 of the invention in which a single phase locked loop is used in the second embodiment of the invention. The phase locked loop operates in the manner described in connection with FIG. 5A.
Phase locked loops can be used in all embodiments of the invention.
FIG. 16 illustrates another embodiment of the invention in which a number of digital signals that may have different data rates can be combined into a combined or mixed digital signal having a data rate that is not necessarily and an integer multiple of any of the data rates of the incoming digital data streams. In circuit 380, a number of digital data streams are supplied to a multiple number of circuit parts 13, 51, 146, 274 or 301. These circuit parts operate as already previously described. As long as each circuit part is clocked using the same clock frequency, the digital data stream on lines 388, 390, . . . 392 will all have the same data rate that can then be combined in summer 394 to provide a combined or mixed digital signal on line 396. In this aspect of the invention, any combination of circuit parts 13, 51, 146, 274 and 301 can be used to provide the digital data streams at the common data rate. This aspect of the invention thus advantageously provides an apparatus for mixing digital signals that may have differing data rates.
FIG. 17 illustrates, in circuit 400 an apparatus for supplying digital signals that may have different data rates from a digital data stream having a single data rate where the data rate of the digital data streams to be output does not need to be an integer multiple of the common digital data rate. As illustrated in FIG. 17, a digital data stream on line 402 having a common data rate is supplied to a multiple number of circuit parts 15, 90, 276, or 303. Each of these circuit parts takes the common data rate and can convert the digital data to digital data streams 404, 406, . . . 408 that may have different data rates. Any combination of circuit parts 15, 90, 276 or 303 can be used in the circuit of FIG. 17.
In both FIGS. 16 and 17, if analog to digital converters were used to supply the input digital signals and/or digital to analog converters were used on the outputs of these circuits, an apparatus that can advantageously digitally combine analog signals to provide a single digital signal or a combined analog signal can be provided.
FIG. 18 illustrates the method of digitally mixing or combining digital signals having differing data rates in accordance with the present invention. In FIG. 18, the method begins in step 420 in which digital data at a first data rate is received. From step 420, the method proceeds to step 422 in which the digital data at the first data rate is converted to digital data at a second data rate in response to a first sigma-delta modulated control signal to provide a first digital data stream at the second data rate. From step 422, the method proceeds to step 424 in which digital data at a third data rate is received. From step 424, the method proceeds to step 426 in which the digital data at the third data rate in converted to digital data at the second data rate in response to a second sigma-delta modulated control signal to provide a second digital data stream at the second data rate. From step 426, the method proceeds to step 428 in which the first and second digital data streams are combined into a single digitally mixed data stream. From step 428, the method proceeds to step 430 in which the digitally mixed data stream is output.
FIG. 19 illustrates the method of the invention for digitally providing different digital data streams from a single digital data stream. The method begins in step 440 in which digital data at a first data rate is received. From step 440, the method proceeds to step 442 in which the digital data at the first data rate is converted to digital data at a second data rate in response to a first sigma-delta modulated control signal. From step 442, the method proceeds to step 444 in which the digital data at the first data rate is converted to digital data at a third data rate in response to a second sigma-delta modulated control signal. From step 444, the method proceeds to step 446 in which the digital data at the second data rate is output. From step 446, the method proceeds to step 448 in which the digital data at the third data rate is output.
For the methods illustrated in FIGS. 18 and 19, converting steps 422, 426, 442, and 444 can be performed as specifically illustrated by the methods illustrated in FIGS. 8 and 11.
In summary, the present invention, in one embodiment, converts an incoming digital data stream to a common data rate by interpolating to create an oversampled signal and then variably decimating the oversampled signal to provide a digital data stream at the common data rate. The common data rate digital data stream is then variably interpolated to create an oversampled signal and then decimated by a fixed decimation ratio to provide a digital data stream at the output having a desired sample rate. In another embodiment, the present invention converts an incoming digital data stream to a common data rate by variably interpolating the incoming digital data stream to provide an oversampled signal and then decimating the oversampled signal by a fixed decimation ratio to provide a digital data stream at the common data rate. The common data rate digital data stream is then interpolated by a fixed ratio to provide an oversampled signal and then variably decimated to provide a digital data stream at the output having a desired sample rate. The present invention can thus convert incoming digital data at any data rate within the working range of the system to an output digital data stream at any arbitrary data rate within the working range of the system.
The present invention may also be used to convert an incoming digital signal to a digital signal having the common data rate. For example, with reference to FIG. 2, an incoming digital signal on line 12 can be converted to a digital signal having a common data rate on line 28. This common rate digital on line 28 can be output as an output signal to be used by other devices that require digital data at the common data rate. This aspect of the present invention is advantageous because it allows digital data streams having differing data rates to be converted to a digital data stream having a common data rate. This same kind of conversion is also provided by all embodiments of the invention. As a result, the present invention provides an advantageous apparatus and method for digitally mixing or combining signals that may have different sample rate. In addition, when the digital signals to be combined are provided by analog to digital converters and reconverted to analog signals by a digital to analog converter as in the co-pending applications incorporated herein by reference, the present invention provides an advantageous apparatus and method for mixing or combining analog signal sources.
In the same manner, the present invention can convert a digital data stream at the common data rate to a digital data stream at any data rate within the working range of the system. For example, with reference to FIG. 2, a digital data stream on line 28 can be converted to a digital data stream at any data rate and output on line 42. This aspect of the present invention is advantageous because it allows the digital data stream on line 28 at the common data rate to be converted to a digital data stream at any other data rate, thus allowing the invention to provide an interface between a common data rate and data rates that may be required by other digital systems. This same kind of conversion is also provided by all embodiments of the invention. In addition, when the digital signal to be interfaced is provided by an analog to digital converter and when the rate-converted digital signals are reconverted to analog signals by digital to analog converters as in the co-pending applications incorporated herein by reference, the present invention provides an advantageous apparatus and method for providing a number of analog signal sources from digital signals that may have different sample rates.
The present invention advantageously converts an incoming digital data stream at any data rate within the working range of the system to an outgoing digital data stream at any data rate within the working range of the system. The data rates of the incoming digital data stream, the outgoing digital data stream, the common data rate, and the clock rate of the system clock do not need to be related by any integer or rational relationship.
Another significant advantage of the present invention is that the digital-to-digital converter does not have to be capable of interpolating the digital data up to the lowest common frequency between the incoming or outgoing digital data rate and the modulator clock frequency. This is due to the sigma-delta modulation of the sampling intervals. Unlike prior art digital-to-digital converters, the sampling interval does not have to correspond exactly to a fixed relationship between the incoming or outgoing digital data rate and the modulator clock. Since the incoming, outgoing, and common sample rates are sigma-delta encoded in the present invention, the sample rates, on average, will represent the desired sample rates with the noise or jitter on the sampling points being pushed into the higher frequency ranges. The present invention thus takes advantage of sigma-delta encoding of the time base to avoid the need for interpolation to very high frequencies, which in the prior art, typically were in the gigahertz range. An additional benefit of this process is that when the present invention is incorporated into an integrated circuit, a significant savings in chip area can be realized by the use of lower interpolation ratios.
Another important advantage of the present invention is that the sigma-delta modulators used to control decimation and interpolation can be clocked using a fixed clock frequency, allowing optimization of the modulator operation at the fixed clock frequency.
Finally, by appropriate combination of sigma-delta control codes in appropriate percentages, an infinite number of sample rates for the output digital data stream can be provided. These sample rates do not need to have any integer or rational relationship with the master clock used to run the digital-to-digital converter or the sample rate of the incoming digital data stream.
Although interpolation has been used herein to explain the method (and an interpolator as the apparatus) by which a digital data stream is converted into a higher sample rate digital data stream, the present invention is not so limited. Any method or apparatus that converts the digital data stream into a higher sample rate digital data stream may be used to practice the invention.
There are many references describing sigma-delta systems. One example is entitled Mixed-Signal Design Seminar published by Analog Devices, Inc., 1991, which is incorporated herein by reference.
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Classification341/61, 341/143International ClassificationH03M1/12, H03M3/02, H03H17/06, H03L7/08, H03M7/36, H03L7/099Cooperative ClassificationH03H17/0614, H03L7/0992, H03L2207/50, H03H17/0628, H03L7/08, H03H17/06European ClassificationH03H17/06C2, H03H17/06, H03H17/06B, H03L7/08, H03L7/099A1Legal EventsDateCodeEventDescriptionOct 7, 2002FPAYFee paymentYear of fee payment: 4Oct 6, 2006FPAYFee paymentYear of fee payment: 8Oct 6, 2010FPAYFee paymentYear of fee payment: 12RotateOriginal ImageGoogle Home - Sitemap - USPTO Bulk Downloads - Privacy Policy - Terms of Service - About Google Patents - Send FeedbackData provided by IFI CLAIMS Patent Services