Source: https://patents.google.com/patent/JP4447372B2/en
Timestamp: 2019-12-09 11:51:00
Document Index: 522977137

Matched Legal Cases: ['art; 106', 'art; 108', 'art; 110', 'art; 112', 'art; 116', 'art; 118', 'art;\n200']

JP4447372B2 - Radio communication system, radio communication device, radio reception device, radio communication method, and channel estimation method - Google Patents
Radio communication system, radio communication device, radio reception device, radio communication method, and channel estimation method Download PDF
JP4447372B2
JP4447372B2 JP2004144179A JP2004144179A JP4447372B2 JP 4447372 B2 JP4447372 B2 JP 4447372B2 JP 2004144179 A JP2004144179 A JP 2004144179A JP 2004144179 A JP2004144179 A JP 2004144179A JP 4447372 B2 JP4447372 B2 JP 4447372B2
JP2004144179A
JP2005328310A (en
キユン シン
2004-05-13 Application filed by 株式会社エヌ・ティ・ティ・ドコモ filed Critical 株式会社エヌ・ティ・ティ・ドコモ
2004-05-13 Priority to JP2004144179A priority Critical patent/JP4447372B2/en
2005-11-24 Publication of JP2005328310A publication Critical patent/JP2005328310A/en
2010-04-07 Publication of JP4447372B2 publication Critical patent/JP4447372B2/en
The present invention generally relates to the technical field of wireless communication, and more particularly to a wireless communication system in which a feedback signal including a channel estimation value is transmitted, and a wireless communication device, a wireless reception device, and a wireless communication method used in such a wireless communication system. And a channel estimation method.
A multi-input multi-output (MIMO) system, which is attracting attention in this kind of technical field, uses a plurality of propagation paths or channels formed by preparing a plurality of transmitting antennas and a plurality of receiving antennas. However, this is a technique for improving the communication capacity. There is a space division multiplexing (SDM) that realizes parallel transmission by transmitting independent signal sequences at the same time and the same frequency band from a plurality of transmission antennas. The signals transmitted in this manner are combined and received by the receiver, but the receiver can perform signal separation using the received signals received by a plurality of antennas. When a certain signal sequence is transmitted from a plurality of transmission antennas, a transmission beam can be formed by multiplying a transmission weight. Furthermore, in MIMO channel signal transmission, it is possible to form a plurality of orthogonal beams between the transceivers by appropriately setting the transmission weight and the reception weight. Therefore, using this property, rather than transmitting an independent transmission signal from each transmission antenna, a plurality of transmission signal sequences (streams) are transmitted using these orthogonal beams. There is a beam space division multiplexing (ESDM: Eigen Beam SDM) system. This ESDM system is advantageous from the viewpoint of reducing inter-stream interference compared to SDM transmission. On the transmission side in the ESDM system, the matrix W based on the eigenvector of the channel matrix is used as the transmission weight, and on the reception side, the conjugate transpose (HW) H of the product of the channel matrix and the eigenmatrix composed of the eigenvector is used as the reception weight. The signal series transmitted from each antenna is detected. Furthermore, from the viewpoint of improving the frequency utilization efficiency, a system that combines an orthogonal frequency division multiplexing (OFDM) method and an ESDM method has also been proposed.
FIG. 1 shows a block diagram of a wireless communication apparatus (explained as a transmitter for convenience) that uses a combination of an ESDM system and an OFDM system. The transmitter 100 includes a first serial-parallel converter 102, a plurality of second serial-parallel converters 104, a number of subcarrier ESDM signal generators 106 used in the OFDM scheme, and a plurality of transmission antennas. A plurality of OFDM modulation units (including an inverse Fourier transform unit, a parallel-serial conversion unit, and a guard interval addition unit) 108 corresponding to each, a plurality of pilot insertion units 110 respectively corresponding to a plurality of transmission antennas, A transmission antenna 112; The transmitter 100 further includes a feedback signal receiving unit 114, a separating unit 116, and a plurality of transmission weight generating units 118 corresponding to each of the plurality of subcarriers. In general, there is a relationship of 1 ≦ N st ≦ min (N, M) between the number of streams N st input to the ESDM signal generator, the number of transmission antennas N, and the number of reception antennas M, where min (N, M) means an operation of selecting the smaller of N and M. For simplicity, N st = N in the following description.
FIG. 2 is a block diagram relating to a wireless communication apparatus (described as a receiver for convenience) that uses a combination of the ESDM system and the OFDM system. The receiver 200 includes a plurality of reception antennas 202, a plurality of OFDM demodulation units (including a guard interval removal unit, a serial-parallel conversion unit, a fast Fourier transform unit, and the like) 204 provided for each reception antenna, and a sub. There are several ESDM signal separators 206 for the number of carriers, third (N) number of third parallel / serial converters 208, and a fourth parallel / serial converter 210. The receiver 200 includes pilot channel estimation units 212 for several reception antennas, a demultiplexing unit 214, reception weight generation units 216 for several subcarriers, and a feedback unit 218.
As shown in FIG. 1, a data signal (data symbol) to be transmitted is converted into a plurality of signal groups (signal series group or stream group) by the first serial-parallel conversion unit 102. Each of the converted streams is further converted into a signal group of several subcarriers by the second serial-parallel conversion unit 104. The converted signal group is given a transmission weight or a weighting coefficient for each subcarrier component by the ESDM signal generator 106 of several subcarriers. This weighting factor makes it possible to distinguish signals transmitted from the transmitting antennas from each other. The weighting factor is determined based on the eigenvalue and eigenvector of the channel matrix. The weighted signal group is modulated by being subjected to fast inverse Fourier transform in the modulation unit 108 of the OFDM system with several transmission antennas. The pilot signals are added to the outputs from the plurality of OFDM modulation units by the first pilot insertion unit 110, and after a guard interval is added, they are wirelessly transmitted from each of the transmission antennas 112.
A signal group received by a plurality of antennas 202 shown in FIG. 2 is separated into subcarrier signals by fast Fourier transform in an OFDM demodulator 204. The signal group for each subcarrier after being demodulated by the OFDM method is separated into a signal group of several transmitting antennas by using the reception weight (weighting factor) in the ESDM signal separation unit 206. The separated signal group is converted into a signal series group (stream group) of several transmission antennas by the third parallel / serial conversion unit 208, and further a single data symbol (stream) is converted by the fourth parallel / serial conversion unit 210. ).
On the other hand, based on a group of signals received by a plurality of receiving antennas 202, a channel impulse response value (CIR: channel impulse response) between the transmitting antenna and the receiving antenna is estimated by pilot channel estimation section 212. This estimation is performed by examining how the known pilot signal on the transmission side and reception side changes in the propagation path. Each channel impulse response value in the present application is represented by h cmn , which indicates an amount related to the c-th subcarrier component among the channel impulse response values between the m-th receiving antenna and the n-th transmitting antenna. In the following description, a symbol having “c” frequently appearing as a subscript indicates that an amount represented by the symbol is an amount related to the c-th subcarrier. The matrix H c whose matrix elements are the individual channel impulse response values h cmn is called a channel matrix and is represented by the following equation.
However, N shows the number of transmitting antennas, and M shows the number of receiving antennas. Information regarding the channel impulse response value is input to the reception weight generation unit 216 prepared for each subcarrier. The reception weight generation unit 216 obtains the eigenvalue λ cn and eigenvector w cn (1 ≦ n ≦ N) of the matrix expressed by H c H H c , and calculates the amount representing (H c w cn ) as the ESDM signal separation unit 206 for each. Here, the operator indicated by the superscript “H” represents taking conjugate transpose. The eigenvector w cn is a vector having several transmission antenna components.
Meanwhile, the c-th sub-carrier component r c included in the received signal,
r c = r c1 +. . . + R cN , where r cn is
r cn = H c w cn s cn
It can be expressed as It can also be expressed as r cn = (r c1n ... R cMn ) T. Here, T represents transposition. s cn represents a signal component related to the c-th subcarrier in the transmitted signal. Accordingly, each of the ESDM signal separation units 206 can obtain the transmitted signal by multiplying the received signal r cn = H c w cn s cn by (H c w cn ) H from the left. Because, between the eigenvalue λ cn and the eigenvector w cn
(H c w cn ) H (H c w cn ) = λ cn
(H c w cn ) H (H c w cj ) = 0 (n ≠ j)
This is because such a relationship is established.
On the other hand, information regarding the channel impulse response value or the channel matrix estimated by the pilot channel estimation unit 212 is fed back to the transmitter side by the feedback unit 218.
Transmitter 100 (FIG. 1) receives information fed back from receiver 200 by feedback signal receiving section 114, and separating section 116 separates it into information for each subcarrier. The separated information is information regarding the channel impulse response value for each subcarrier, and is provided to the transmission weight generation unit 118 corresponding to each subcarrier. The transmission weight generation unit 118 calculates a weight coefficient w cn for each subcarrier. The transmitter 100 updates the weighting factor by using this weighting factor for the next transmission instead of the previously used weighting factor.
The ESDM wireless communication technology is described in Non-Patent Document 1, for example.
Thus, the feedback signal is transmitted from the receiver to the transmitter because the channel estimate h for the forward link from the transmitter to the receiver and the channel estimate h for the reverse link from the receiver to the transmitter. This is because 'is generally different (symbol suffixes are omitted). That is, it is assumed that a frequency division multiplexing (FDD) method is used. In a time division multiplexing (TDD) method in which channel estimation values are equal in the upper and lower links, it is not essential to transmit a feedback signal.
FIG. 3 shows a detailed block diagram of the feedback unit 218 of the receiver shown in FIG. As shown in the figure, channel information representing the channel estimation value h is quantized to a quantization level suitable for the feedback signal by the feedback discretization unit. This quantization level is coarser than the quantization level used to represent the channel information input to the feedback discretization unit in order to reduce the information amount of the feedback signal. The quantized binary signal is subjected to error correction coding processing in the coding unit and output to the interleaving unit. The signal whose signal order is rearranged in the interleave unit is mapped to an appropriate symbol in the symbol map unit. The mapped signal is multiplexed with the pilot signal. The multiplexed signal is converted into a plurality of parallel signals by the serial-parallel converter (S / P) in the OFDM modulation unit shown in the broken line frame, and the inverse Fourier transform is performed in the OFDM modulation unit. Is done. In this way, a feedback signal including channel information is created and transmitted to the transmitter side. When the single carrier method is adopted instead of the OFDM method, the serial / parallel conversion unit (S / P) and the IFFT unit shown in the broken line frame in the figure are omitted.
FIG. 4 shows a detailed block diagram of the feedback signal receiver 114 of the transmitter shown in FIG. As shown in the figure, the received feedback signal is Fourier-transformed by the OFDM demodulator shown in the broken line frame, converted into a signal group in the frequency domain, and sent to the parallel-serial converter (P / S). Converted into a serial signal. Channel estimation and channel compensation are performed based on this signal. Based on the signal after channel compensation, symbol determination is performed in the demapping unit. The signals after the determination are rearranged in a predetermined order by the deinterleave unit. The rearranged signal is subjected to error correction decoding by the decoding unit, and a channel estimation value h reproduced based on the bit sequence of the decoding result is output from the channel reproduction unit. In addition, when the single carrier system is adopted instead of the OFDM system, the FFT unit and the parallel / serial conversion unit (P / S) shown in the broken line frame in the figure are omitted.
Miyashita et al., IEICE, IEICE RCS2002-53
Thus, a large amount of signal and a large amount of signal processing are required for transmission and reception of the feedback signal. In the FDD ESDM transmission system, it is necessary to feed back all channel information from the receiver to the transmitter, and the amount of feedback is particularly large. For this reason, there is a concern that resources for transmitting data signals other than the feedback signal may be reduced. Further, when wireless communication is performed in a wide band, more feedback signals are transmitted, and the above-mentioned concern is further deepened.
The present invention has been made in order to address at least one of the above-described problems, and a problem thereof is a radio communication system, a radio communication apparatus, and a radio reception apparatus that reduce a transmission amount of a feedback signal including a channel estimation value. It is to provide a wireless communication method and a channel estimation method.
According to one embodiment, a wireless communication system is used in which a feedback signal including at least a channel estimate is transmitted between the first and second wireless communication devices .
The first wireless communication device that transmits a feedback signal includes:
Channel estimation means for receiving a signal including a pilot signal and obtaining a channel estimation value of the radio link;
Multiplying means for multiplying a pilot signal by the channel estimation value;
A second wireless communication device that receives the feedback signal, and includes a multiplexing unit that multiplexes the output signal from the multiplication unit and the pilot signal and creates a feedback signal.
Separating means for separating a plurality of signals multiplexed in the feedback signal;
Based on the separated plurality of signals, Ru and means for obtaining the channel estimates of the radio link in transmitting from the second radio communication device to the first wireless communication device.
According to the present invention, it is possible to reduce the transmission amount of a feedback signal including a channel estimation value.
According to one aspect of the present invention, a radio communication apparatus that receives a feedback signal by using a feedback signal in which a pilot signal weighted with channel information and a pilot signal not weighted with channel information are multiplexed is used. Thus, desired channel information can be easily obtained.
According to an aspect of the present invention, means for code-spreading a channel information signal before being multiplied by a pilot signal is provided in an OFDM wireless communication apparatus. Thereby, fading tolerance in the case where the channel estimation value for each subcarrier is wirelessly transmitted can be enhanced.
According to one aspect of the present invention, an interleaver that arranges signals indicating channel estimation values before multiplication with pilot signals in a predetermined order is provided in an OFDM wireless communication apparatus. Thereby, it is possible to prevent signals representing the same channel estimation value from being mapped to adjacent subcarriers as much as possible.
According to an aspect of the present invention, a multiplexed signal is separated into a radio receiver that receives a feedback signal in which a channel estimation value and a pilot signal are multiplied and a pilot signal is multiplexed. Means for determining a reverse link channel estimate from the generated signal and determining a forward link channel estimate from the separated separate signal and the channel estimate. Thereby, channel information can be acquired more easily than before.
According to an aspect of the present invention, an MMSE filter that obtains a forward link channel estimation value from a reverse link channel estimation value is provided in the radio reception apparatus. Thereby, channel information can be estimated with high accuracy.
According to an aspect of the present invention, the wireless communication apparatus further includes means for normalizing a signal indicating the channel estimation value of the forward link before being input to the multiplying means by a predetermined scale factor. Thereby, the amplitude of the signal indicating the channel estimation value can be kept within a desired range, and the influence of nonlinear distortion, noise, and the like can be suppressed.
According to an aspect of the present invention, the wireless communication apparatus further includes means for replicating a signal indicating the channel estimate value of the forward link before being input to the multiplying means into a plurality of signals. Since signals having the same content are transmitted as a feedback signal a plurality of times, it is possible to increase the reception energy per channel information representing the channel estimation value and improve the signal quality. According to an aspect of the present invention, means for averaging a plurality of signals indicating channel estimation values is further provided in the wireless communication apparatus. By performing the averaging, the signal quality can be improved.
According to one aspect of the invention, an amount indicative of the absolute level of the received signal or an amount indicative of the reference power is transmitted with or separately from the feedback signal. As a result, the communication apparatus that has received the feedback signal or the like can measure not only the relative magnitude of the channel estimation value but also the absolute magnitude, and therefore can measure signal quality such as SNR.
Hereinafter, various embodiments according to the present invention will be described with reference to the drawings. In each figure, the same reference number is attached | subjected to the element which has the same structure and function.
FIG. 5 is a schematic diagram of an FDD wireless communication system according to an embodiment of the present invention. In the figure, a first wireless communication device 510 that transmits a feedback signal and a second wireless communication device 520 that receives the feedback signal are depicted. The first and second wireless communication devices are ESDM devices in this embodiment, but may be any devices that transmit and receive channel information as feedback signals. First radio communication apparatus 510 includes pilot signal generation section 512, multiplexing section 514, and multiplication section 516. The second wireless communication apparatus includes a separation unit 522, a first estimation unit 524, a second estimation unit 526, and a pilot signal generation unit 528. For convenience of explanation, a radio link from the second radio communication apparatus 520 to the first radio communication apparatus is called a forward link, and a radio link in the reverse direction is called a reverse link. Channel information on the forward link (channel estimate or channel impulse response value) is represented by h, and channel information on the reverse link is represented by h '. Note that channel information and channel estimation value are used synonymously.
Pilot signal generation section 512 of first wireless communication apparatus 510 generates a known pilot signal on the transmission side and reception side. The pilot signal may be called a known signal, a reference signal, a training signal, or the like. The pilot signal generation unit 512 outputs two pilot signals s 1 and s 2 . These may have different signal contents or the same contents. This is because both the transmission side and the reception side need only be known. In the following description, they will be described separately as the first pilot signal s 1 and the second pilot signal s 2 . The first pilot signal s 1 is supplied to one input of the multiplexing unit 514. However, as will be described later, it is desirable that the two pilot signals have the same content from the viewpoint of reducing the signal processing burden.
Multiplier 516 multiplies the signal representing channel information h by second pilot signal s 2 and outputs multiplication result hs 2 . The output multiplication result is given to the other input of the multiplexing unit 514.
The multiplexing unit 514 creates a feedback signal by temporally multiplexing the two input signals s 1 and hs 2 . For example, the multiplexing unit 514 inserts these two signals into two adjacent or separated time slots, and performs multiplexing.
Separating section 522 of second wireless communication apparatus 520 individually separates the signals multiplexed in the received feedback signal. One separated signal r f1 is provided to one input of the first estimation unit 524. The other separated signal r f2 is provided to one input of the second estimation unit 524.
Pilot signal generation section 528 provides first pilot signal s 1 to the other input of first estimation section 524. Pilot signal generation section 528 provides second pilot signal s 2 to the other input of second estimation section 526.
The first estimation unit 524 calculates a reverse link channel estimation value h ′ based on the one signal r f1 separated by the separation unit 522 and the first pilot signal s 1, and outputs the channel estimation value h ′. .
Second estimation unit 526, and other signal r f2 separated by the separation unit 522, the second pilot signal s 2, based on the channel estimation value h 'of the reverse link channel estimate for the forward link Calculate h and output it.
The operation will be described next. First, it is assumed that the first and second wireless communication devices 510 and 520 perform wireless communication. First wireless communication apparatus 510 transmits a feedback signal including forward link channel information h to second wireless communication apparatus 520. The channel information h to be transmitted can be estimated by a channel estimation unit (not shown) based on the pilot signal received from the second wireless communication apparatus 520. This pilot signal may be the same as or different from the first and second pilot signals. What is necessary is just to be known by both.
The channel information h is multiplied by the second pilot signal s 2 in the multiplication unit 516, and the multiplication result hs 2 is given to the other input of the multiplexing unit 514. Multiplexer 514 creates a feedback signal by multiplexing first pilot signal s 1 acquired from one input and multiplication result hs 2 acquired from the other input. The feedback signal is transmitted to the second wireless communication device 520 through the reverse wireless link h ′.
A reception signal (feedback signal) received by the second wireless communication apparatus 520 and input to the separation unit 522 includes the two multiplexed signals described above. That is, the received signal includes a first received signal r f1 related to the first pilot signal and a second received signal r f2 related to the second pilot signal, which are separated by the separation unit 522. This received signal is affected by the reverse link channel h ′. Therefore,
r f1 = h's 1 (A)
r f2 = h'hs 2 (B)
It can be expressed as The first estimation unit 524 calculates the reverse link channel estimation value h ′ by dividing the first reception signal r f1 = h ′s 1 by the first pilot signal s 1 . When the first pilot signal is composed of a plurality of symbols, the first estimation unit may obtain a channel estimation value for each symbol and average them. The second estimation unit 526 divides the second received signal r f2 = h′hs 2 by the channel estimation value h ′ of the reverse link and the second pilot signal s 2 , thereby performing channel estimation of the forward link. The value h is calculated.
As described above, according to the present embodiment, the feedback signal is obtained by using the feedback signal in which the pilot signal hs 2 weighted with the channel information h and the pilot signal s 1 not weighted with the channel information are used. The channel information of the forward link can be easily obtained in the wireless communication device that receives
In the illustrated example, the first and second estimation units 524 and 526 are depicted as separate functional blocks for convenience of explanation, but this is not essential to the present invention. For example, in order to obtain the channel information h of the forward link,
(R f2 · s 1 ) / (r f1 · s 2 ), (r f2 / r f1 ) · (s 1 / s 2 ), etc. may be calculated. Based on the equations (A) and (B), any method for deriving the forward link channel information h can be used. If the contents of the first and second pilot signals are the same (s 1 = s 2 ), the forward link channel information h can be obtained simply by simply calculating r f2 / r f1. Can do.
In order to obtain the channel information h of the forward link, in the conventional method, the channel information is transmitted through processes such as discretization for feedback, encoding, symbol map, etc. (FIG. 3), and the reverse processing is performed on the receiving side. (Fig. 4). On the other hand, in the present embodiment, a pilot signal weighted by channel information h of the forward channel and a pilot signal not weighted in such a manner are transmitted, and the channel information is derived based on them on the receiving side. Is done. For this reason, the feedback signal amount and the signal processing amount are greatly reduced. According to the present embodiment, channel information can be easily obtained by simple signal processing, unlike the conventional method requiring complicated digital signal processing. For example, assume that the number of transmission antennas and the number of reception antennas are both four and the number of FFT points is 64. In this case, in this embodiment, the number of signals or the number of symbols transmitted / received by the feedback signal is 64 × 4 × 4 = 1024. However, in the conventional method, the number of quantization levels for discretization is 2 5 = 32 (10 bits in total of I component and Q component), the coding rate is 3/4, and the modulation method is 64 QAM (6 per symbol). Bit), the number of signals transmitted and received by the feedback signal is 64 × 4 × 4 × (10/6) ÷ (3/4) ≈2275. Therefore, according to the present embodiment, the amount of feedback signal can be reduced to about half of the conventional amount. However, these numerical values are only examples. According to the present embodiment, the calculation burden related to transmission / reception of the feedback signal is reduced, so that the feedback signal is communicated promptly, and the delay of the feedback signal is shortened compared to the conventional case.
FIG. 6 shows first and second wireless communication devices 610 and 620 used in a wireless communication system according to an embodiment of the present invention. Similarly to the case of FIG. 5, the first wireless communication apparatus 610 transmits a feedback signal including the channel information h of the forward link, and the second wireless communication apparatus 620 receives it. In the first wireless communication apparatus 610 in the present embodiment, an OFDM modulation unit 612 connected to the multiplexing unit 514 is provided. The OFDM modulation unit 612 includes a serial-parallel conversion unit (S / P) 614 and a fast inverse Fourier transform unit 616. The second wireless communication apparatus 620 is provided with an OFDM demodulator 622 connected to the separator 522. The OFDM demodulation unit 622 includes a fast Fourier transform unit 624 and a parallel / serial conversion unit (P / S) 626.
In this embodiment, modulation / demodulation by the OFDM method is performed. The feedback signal transmitted from the first wireless communication apparatus 610 is modulated by the OFDM modulation unit 612 and wirelessly transmitted. Second radio communication apparatus 620 demodulates the received signal by OFDM demodulation section 622 and calculates forward link channel information h by the same method as described with reference to FIG.
In the first and second embodiments, the channel information h is input to the multiplication unit 516 as it is. However, it operates in a linear power range of the amplifier, from the viewpoint of suppressing the influence of noise, it is desirable to normalize the amplitude a x of the signal representing the channel information. The normalization coefficient c multiplied by the signal expressing the channel information can be determined by various methods. For example, the normalization coefficient c is from the viewpoint of limiting the maximum value.
c = (max (a x) / A MAX) -1
It is good. Here, max (a x ) represents the maximum value of the amplitude a x , and A MAX represents a predetermined upper limit value. Further, the normalization coefficient c is from the viewpoint of making the average value constant.
c = ((Σa x) / N x) -1 A v
It is good. Here, N x represents the number of samples for performing averaging, A v is a predetermined constant.
FIG. 7 is a block diagram of a wireless communication apparatus 700 that transmits a feedback signal according to an embodiment of the present invention. In general, in this embodiment, code-spread channel information is multiplied by a pilot signal, multiplexed with the same or another pilot signal, and transmitted after modulation of the OFDM scheme. The wireless communication apparatus 700 includes an encoding parameter determination unit 702, a code generation unit, in addition to the pilot signal generation unit 512, the multiplication unit 516, the multiplexing unit 514, and the OFDM modulation unit 612 described in the first and second embodiments. 704, a spread multiplexing unit 706, an interleave unit 708, a normalization coefficient determination unit 710, and a normalization unit 712. The diffusion multiplexing unit 706 further includes a serial / parallel conversion unit (S / P) 762, a plurality of spreading units 766, and a combining unit (Σ) 768.
The encoding parameter determination unit 702 determines parameters such as the code length and the number of multiplexed codes used for encoding. The code length corresponds to the length of the code multiplied by the spreading unit 766. The number of multiplexing corresponds to the number of spreading units 766. The code generation unit 704 generates a code to be used using the parameter determined by the encoding parameter 704. The serial / parallel conversion unit 762 in the spread multiplexing unit 706 parallelizes the input signal (channel information) according to the number specified as the multiplexing number. Each spreading section 766 multiplies one of the parallel signals (one signal series) by a code. The combining unit 768 combines the encoded signals into one. By changing the code length and the number of multiplexing, it is possible to adjust the transmission power amount per channel information, the accuracy of the feedback signal, and the like. Further, the normalization coefficient c may be determined according to the code length and the number of multiplexing. Furthermore, the encoding parameter may be changed as appropriate based on a signal quality parameter such as a signal-to-noise power ratio (SNR). Such signal quality parameters may be common to the forward link and the reverse link, or may be distinguished between them.
Interleaving section 708 changes the signal sequence according to a predetermined rule. As a result, it is possible to reduce the occurrence of similar fading by mapping symbols indicating the same channel information to adjacent subcarriers.
The normalization coefficient determination unit 710 determines the normalization coefficient c as described in the third embodiment. The normalization unit 712 multiplies the input signal by the determined normalization coefficient c and supplies the result to the multiplication unit 516.
FIG. 8 is a block diagram of a wireless communication device 800 that receives a feedback signal according to an embodiment of the present invention. In general, in the present embodiment, the received feedback signal is demodulated by OFDM, channel estimation is performed, deinterleaved, despread, and channel information is derived. The radio communication apparatus 800 includes a deinterleave unit 802 in addition to the OFDM demodulator 622, the demultiplexer 522, the first and second estimators 524 and 526, and the pilot signal generator 528 described in the first and second embodiments. And a despreading unit 804. The despreading unit 804 includes a serial / parallel conversion unit (S / P) 842, a code generation unit 844, a plurality of despreading units 846, and a combining unit 848. Elements related to demodulation and channel estimation in the OFDM scheme have been described and will not be further described.
The deinterleaving unit 802 changes the signal arrangement according to a predetermined rule. The predetermined rule corresponds to the rule used in the interleave unit 708 in FIG.
The code generation unit 844 of the despreading unit 804 generates the same code as that generated by the code generation unit 704 of FIG. The serial / parallel converter (S / P) 842 converts the input signal into a plurality of parallel signals. Each despreading unit 846 multiplies one of the parallel signals by a code, performs despreading, and outputs channel information h.
In a communication system that employs a multi-carrier scheme such as the OFDM scheme, since the state of the channel differs for each subcarrier, it is necessary to obtain a channel estimation value for each subcarrier and transmit them using a feedback signal. In the process of propagation of the feedback signal by radio, it is often subjected to selective fading in the frequency direction. For this reason, there is a possibility that information on a certain subcarrier is greatly affected by noise. In this case, the receiving side cannot accurately obtain the channel estimation value. The wireless communication system according to the present embodiment copes with the problem caused by frequency selective fading by performing encoding and interleaving and processing corresponding to them. First, channel information is spread over a wide frequency range by the spread multiplexing unit 706 and the interleave unit 708 of FIG. Thereby, the tolerance with respect to the fading of a frequency direction can be improved rather than before. The spread signal may be input to the normalization unit 712 and the multiplication unit 516. In this embodiment, the signal is supplied to the interleaving unit 708 in order to further improve fading resistance. This interleaving suppresses that symbols indicating the same channel estimation value are mapped to relatively close subcarriers, so that they are excessively influenced by noise due to fading.
In the present embodiment, the interleaving unit 708 performs interleaving to suppress mapping of similar signals to adjacent subcarriers as much as possible. The interleaved signal is appropriately normalized by the normalization unit 712 and then input to the multiplication unit 516, and a feedback signal is formed by the method already described. On the receiving side, the received feedback signal is demodulated by the OFDM method, and channel estimation is performed. The estimated signal is input to the deinterleaving unit 802 in FIG. 8, despread by the despreading unit 804, and channel information h is derived.
FIG. 9 is a block diagram of wireless communication apparatuses 901 and 911 used in a wireless communication system according to an embodiment of the present invention. The wireless communication device 901 transmits a feedback signal, and the wireless communication device 911 receives the feedback signal.
The wireless communication apparatus 901 includes a repetition determining unit 902 and a duplicating unit 904 in addition to the pilot signal generating unit 512, the multiplying unit 516, the multiplexing unit 514, the OFDM modulation unit 612, and the interleaving unit 708 that have already been described. The wireless communication apparatus 911 includes an averaging unit 910 in addition to the already described OFDM demodulation unit 622, separation unit 522, first and second estimation units 524 and 526, pilot signal generation unit 528, and deinterleave unit 802. Have. Since elements related to modulation / demodulation and channel estimation in the OFDM system have been described, they will not be further described.
Duplication unit 904, the input signal is replicated on the basis of the number of repetitions N d determined by the repetition number determination section 902. For example, duplication unit 904 channel information h is input, a signal representative of the channel information h and outputs a plurality (N d number) continuous signal sequence. Information on the number of repetitions is also notified to the interleave unit 708, the pilot signal generation unit 512, and the like. After interleaving, the channel information duplicated by duplicating section 904 is multiplied by the pilot signal by multiplication section 516, multiplexed with the same or another pilot signal by multiplexing section 514, and then transmitted to modulation section 612 of the OFDM system. After being subjected to inverse Fourier transform, it is transmitted as a feedback signal.
The feedback signal received on the receiving side is subjected to fast Fourier transform in the OFDM demodulator 622, channel estimation is performed in the first and second estimators 524 and 526, and deinterleaved in the deinterleaver 802. Input to the averaging unit 910. The averaging unit 910 outputs more accurate channel information by averaging channel information obtained by the number of copies determined by the number of repetitions 902.
According to the present embodiment, the channel information to be fed back by the feedback signal is repeatedly transmitted a desired number of times, so that the reception energy per channel estimation value can be increased several times to improve the accuracy of the feedback signal. it can.
FIG. 10 shows a combination of standardizing a signal representing channel information (second embodiment), code multiplexing (fourth embodiment), interleaving (fourth embodiment), and duplicating (fourth embodiment). 1 shows a wireless communication device 1001 that transmits a feedback signal and a wireless communication device 1011 that receives such a feedback signal and performs reverse signal processing. The parameter determination unit 1002 determines various parameters such as the code length and multiplexing number of codes used for encoding, and the multiplexing number of channel information, and notifies them to related elements. By forming such a wireless communication device, the benefits described in the embodiments can be enjoyed. Thereby, the accuracy of the feedback signal can be controlled more precisely. For example, the received energy per channel estimation value can be increased or decreased more flexibly (integer multiple or non-integer multiple) by adjusting the code length, multiplexing number, and repetition rate.
In the examples described in the fourth and fifth embodiments, channel information is finally detected by despreading. However, from the viewpoint of further improving the accuracy in the ESDM wireless communication system, the channel information may be estimated by a least mean square error method (MMSE) instead of simply despreading. In this case, the channel information of the forward link is
w l H r / | w l H X l |
It is calculated by. Here, l indicates a parameter for designating a stream. r f is the received feedback signal. wl is a quantity determined by the following formula:
Here, σ is noise power, I is a unit matrix, and X 1 is an element forming a product HC of a channel matrix H and a matrix C composed of spreading codes.
The spreading code used on the channel estimates h l to feedback,
c l = [c l1 c l2 ... c lNs ]
And When h l is diffused by c l,
[C l1 c l2 ... C lNs ] T × h l s l
N s transmission symbols expressed as follows. N s represents the spreading code length. When the value of the feedback channel to be sent with c l0 and h 0 ', the received signal r l for h l is
r l = [h 1 'c l1 h 2' c l2 ··· h Ns' c lNs] T × h l s l
X l = [h 1 'c l1 h 2 ' c l2 ... H Ns ' c lNs ] T
Then, the received signal r of the spread multiplex signal is
r = X 1 h 1 s 1 + X 2 h 2 s 2 +... + XL L h L s L
It is expressed. L represents the diffusion multiplexing number.
If the number of duplications in the fifth embodiment that performs duplication is N d , one channel information h 1 is transmitted through a plurality of (N d ) channels. These channels,
[H 1 ′ h 2 ′... H Nd ′] T , and the above w is
w = [h 1 'h 2 '... h Nd '] T
Then, processing can be performed in the same manner as described above. However, since diffusion multiplexing is not performed, it should be noted that the subscript “l” is omitted in the formula for w.
Further, when the code spreading for the fourth embodiment is combined with the duplication for the fifth embodiment, one channel estimate is transmitted through N d × N s channels. the received signal r l for h l is,
r l = [h 1 c l1 h 2 c l2 ... h Ns c lNs
h (Ns + 1) c l1 h (Ns + 2) c l2 ... h (Ns + Ns) c lNs
··· h (Nd × Ns) c lNs] T × h l s l
X l = [h 1 'c l1 h 2' c l2 ··· h l (Nd × Ns) 'c lNs] T
Then, the received signal r of the spread multiplexed signal is
When interleaving is performed, it is necessary to rearrange the matrix elements in accordance with the interleaving method used.
By the way, normalization in the third embodiment or the like is advantageous from the viewpoint of performing signal processing at an appropriate amplitude level. However, for example, when a plurality of pieces of channel information are transmitted in an OFDM wireless communication system, the absolute reception level P n of each channel cannot be known, and the relative reception level P n ′ of each channel is not known. Can only know. Therefore, for example, it is not easy to know the signal quality based on the feedback signal. In this embodiment, the feedback signal described in the above embodiment includes an amount indicating an absolute reception level or an amount for deriving it, or such an amount is transmitted separately from the feedback signal. The In any case, such a quantity is transmitted to the receiving side. The amount indicating the absolute reception level or the like may be a power reference, and may be the average power of the entire signal related to all subcarriers or may be the signal power related to a specific subcarrier. . The wireless communication apparatus that has acquired this absolute reception level together with the feedback signal can know the absolute signal power P n for each subcarrier using this reception level. For example, when P n ′ is acquired as the reception level of subcarrier n from the feedback signal and the absolute reception level P 1 of subcarrier 1 is acquired, the absolute reception level P n regarding subcarrier n is P n = P n ′ × P 1 ′ / P 1 When such an absolute reception level is found, an amount indicating signal quality such as SNR can be calculated based on the absolute reception level. Based on this SNR, the modulation scheme, encoding scheme, and the like may be changed as appropriate.
1 is a block diagram related to an ESDM transmitter. FIG. 1 is a block diagram related to an ESDM receiver. FIG. A detailed block diagram of the feedback unit is shown. The detailed block diagram of a feedback signal receiving part is shown. 1 shows a schematic diagram of a wireless communication system according to one embodiment of the present invention. 1 shows a schematic diagram of a wireless communication system according to one embodiment of the present invention. 1 is a block diagram of a wireless communication apparatus according to an embodiment of the present invention. 1 is a block diagram of a wireless communication apparatus according to an embodiment of the present invention. 1 shows a schematic diagram of a wireless communication system according to one embodiment of the present invention. 1 shows a schematic diagram of a wireless communication system according to one embodiment of the present invention.
DESCRIPTION OF SYMBOLS 100 Transmitter; 102,104 Series-parallel conversion part; 106 ESDM signal generation part; 108 OFDM system modulation part; 110 Pilot insertion part; 112 Transmission antenna; 114 Feedback signal reception part; 116 Separation part; 118 Transmission weight generation part;
200 receiver; 204 OFDM demodulator; 206 ESDM signal separator; 208, 210 parallel-serial converter; 212 pilot channel estimator; 214 demultiplexer; 216 reception weight generator; 218 feedback unit;
510, 520 wireless communication apparatus; 512 pilot signal generation unit; 514 multiplexing unit; 516 multiplication unit; 522 demultiplexing unit; 524 first estimation unit; 526 second estimation unit; 528 pilot signal generation unit;
612 OFDM modulation unit; 614 serial-parallel conversion unit; 616 fast inverse Fourier transform unit; 622 OFDM demodulation unit; 624 fast Fourier transform unit; 626 parallel-serial conversion unit;
702 Coding parameter determination unit; 704 Code generation unit; 706 Spreading multiplexing unit; 708 Interleaving unit; 710 Normalization coefficient determination unit; 712 Normalization unit; 762 Series parallel conversion unit; 766 Spreading unit;
802 Deinterleaving unit; 804 Despreading unit; 842 Series-parallel converting unit; 846 Despreading unit; 848 Combining unit 901, 911 Wireless communication device; 902 Repetition number determining unit; 904 Duplicating unit; 910 Averaging unit;
1001, 1011 wireless communication device; 1002 parameter determination unit
A wireless communication system in which a feedback signal including at least a channel estimation value is transmitted between first and second wireless communication devices,
Means for obtaining a channel estimation value of a radio link when transmitting from the second radio communication device to the first radio communication device based on the plurality of separated signals. .
Receiving means for receiving a signal including a pilot signal;
Channel estimation means for obtaining a forward link channel estimate from the signal received by the receiving means;
Multiplying means for multiplying the channel estimate by a pilot signal;
A radio communication apparatus comprising: a multiplexing unit that multiplexes an output signal and a pilot signal from the multiplication unit to create a feedback signal; and a transmission unit that transmits the feedback signal.
The radio communication apparatus according to claim 2, further comprising means for modulating an output signal from the multiplication means and a signal multiplexed with a pilot signal by an orthogonal frequency division multiplexing (OFDM) system.
3. The wireless communication apparatus according to claim 2, further comprising means for code-spreading a signal indicating a channel estimation value before being multiplied by the multiplication means.
The radio communication apparatus according to claim 2, further comprising: an interleaver that arranges signals indicating channel estimation values before being multiplied by the multiplication unit in a predetermined order.
Receiving means for receiving a feedback signal in which the forward link channel estimate and the pilot signal multiplied signal and the pilot signal are multiplexed;
Means for obtaining a channel estimation value of a forward link based on the plurality of separated signals.
Means for determining a channel estimate for the forward link;
Means for determining a reverse link channel estimate from a signal separated by the separation means;
7. The radio receiving apparatus according to claim 6, further comprising: means for obtaining a channel estimate value of a forward link from another signal separated by the separation means and the channel estimate value.
The radio receiving apparatus according to claim 6, further comprising: a unit that demodulates a signal received by the receiving unit using an orthogonal frequency division multiplexing (OFDM) method.
The radio receiving apparatus according to claim 6, further comprising means for code despreading a signal including a channel estimation value of the forward link.
The radio reception apparatus according to claim 6, further comprising: a deinterleaver that arranges signals including channel estimates of the forward link in a predetermined order.
The radio receiving apparatus according to claim 6, further comprising: an MMSE filter that obtains a channel estimate of the forward link from a channel estimate of the reverse link by a least square error (MMSE) method.
Obtain the channel estimate of the forward link from the received signal including the pilot signal,
A feedback signal is created by multiplexing a signal obtained by multiplying a pilot signal by the channel estimation value and a pilot signal,
The wireless communication method, wherein the feedback signal is transmitted.
Receiving a feedback signal in which the forward link channel estimate and the pilot signal multiplied signal and the pilot signal are multiplexed;
Separating a plurality of signals multiplexed in the feedback signal individually;
A channel estimation method, comprising: obtaining a channel estimation value of a forward link based on a plurality of separated signals.
JP2004144179A 2004-05-13 2004-05-13 Radio communication system, radio communication device, radio reception device, radio communication method, and channel estimation method Active JP4447372B2 (en)
JP2004144179A JP4447372B2 (en) 2004-05-13 2004-05-13 Radio communication system, radio communication device, radio reception device, radio communication method, and channel estimation method
EP05252917.9A EP1596549B1 (en) 2004-05-13 2005-05-12 Wireless communication system, wireless communication device, wireless reception device, wireless communication method, and channel estimation method
US11/128,190 US7684476B2 (en) 2004-05-13 2005-05-13 Wireless communication system and method with feedback signals containing channel estimate values
CN 200510069356 CN1697361A (en) 2004-05-13 2005-05-13 Wireless communication system, wireless communication device, wireless reception device, wireless communication method, and channel estimation method
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JP2004144179A Active JP4447372B2 (en) 2004-05-13 2004-05-13 Radio communication system, radio communication device, radio reception device, radio communication method, and channel estimation method
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