Source: https://patents.google.com/patent/JP5654253B2/en
Timestamp: 2020-01-20 21:41:01
Document Index: 257507444

Matched Legal Cases: ['art 11', 'art 2', 'art 14', 'art 2', 'art 11', 'art 2', 'art 2', 'art 14', 'art 3', 'art 4', 'art 6', 'art 12', 'art 13', 'art 14', 'art 15', 'art 16']

JP5654253B2 - Obstacle detection device - Google Patents
JP5654253B2
JP5654253B2 JP2010066238A JP2010066238A JP5654253B2 JP 5654253 B2 JP5654253 B2 JP 5654253B2 JP 2010066238 A JP2010066238 A JP 2010066238A JP 2010066238 A JP2010066238 A JP 2010066238A JP 5654253 B2 JP5654253 B2 JP 5654253B2
JP2010066238A
JP2011196924A (en
寺田　直人
2010-03-23 Application filed by パナソニックＩｐマネジメント株式会社 filed Critical パナソニックＩｐマネジメント株式会社
2010-03-23 Priority to JP2010066238A priority Critical patent/JP5654253B2/en
2011-10-06 Publication of JP2011196924A publication Critical patent/JP2011196924A/en
2015-01-14 Publication of JP5654253B2 publication Critical patent/JP5654253B2/en
The present invention relates to an obstacle detection device that detects an obstacle using a signal wave propagating in space.
Conventionally, an obstacle is detected using a signal wave propagating in a space such as a microwave. For example, the high-frequency signal from the transmission circuit is turned on / off to be pulsed and transmitted toward the outside of the apparatus, the reflected wave due to the obstacle of the transmission is received, and the high-frequency signal and the reception wave from the transmission circuit are received. And AM detection, the obtained detection waveform is differentiated by a differentiation circuit, the rising edge of the reflected wave is detected from the positive differential output, the reception start time is obtained, and the reception start time and known transmission An obstacle detection device that acquires a time difference from a start time, calculates a distance to an object based on the time difference, and detects an obstacle is known (see, for example, Patent Document 1). In this apparatus, in order to acquire the time difference, a voltage-time conversion process of a sawtooth waveform is performed, or a process of counting the number of sampling pulses is performed.
Here, with reference to FIG. 16, FIG. 17, the general example of the prior art which acquires the said time difference using a pulse counter, and calculates | requires the distance to an obstruction is demonstrated. As shown in FIG. 16, the circuit portion related to the time difference acquisition includes a transmission unit 91, a reception unit 92, a clock generation unit 93, and a counter 94. For example, it is assumed that the reception start time is detected by differential output as described above. Based on the information on the transmission start time from the transmission unit 91 and the information on the reception start time from the reception unit 92, the counter 94 counts the number of clock pulses (n Count). The time difference δT to be obtained is the time difference between the rising times of the transmission signal and the reception signal as shown in FIGS. 17A and 17B, and the clock pulse is larger than the time difference δT as shown in FIG. 17C. This is a pulse train of high frequency (frequency fc = 1 / Tc) with a sufficiently short period Tc. As shown in FIG. 17D, the counter 94 obtains the time t1 = n / fc = n × Tc as the measured value of the time difference δT. The time t1 is a round trip time to the obstacle of the signal wave, and the distance L to the obstacle is obtained by L = c × t1 / 2.
However, in order to obtain the distance L, in the obstacle detection device using the time t1, which is a measured value of the time difference δT as shown in Patent Document 1 and FIGS. In addition, it is necessary to increase the frequency fc of the clock pulse. In the above-mentioned distance L = c × t1 / 2, c is the propagation speed of a signal wave (radio wave, light, ultrasonic wave, etc.), and when the signal wave is a radio wave or light, c≈3 × 10 8 m. The distance error ΔL is ΔL = c / fc / 2. Therefore, for example, when fc = 150 MHz, ΔL = 1 m. In order to improve the distance error ΔL to 5 cm, it is necessary to set the frequency of the clock pulse to fc = 3 GHz. In general, an electric circuit is more expensive as the frequency is higher. If the actual circuit configuration is increased in speed, it becomes an expensive circuit configuration, which is not economical.
The present invention solves the above-described problems, and enables low-cost obstacle detection that can accurately determine the distance to an obstacle using signal waves such as light, radio waves, and ultrasonic waves with a simple configuration. An object is to provide an apparatus.
An obstacle detection device according to the present invention is a signal obtained by amplitude-modulating a predetermined carrier wave with a transmission signal having a first frequency in an obstacle detection device that detects an obstacle using a signal wave propagating in space. A transmitter that generates a wave and transmits the signal wave to space, a receiver that receives a reflected wave from an obstacle of the signal wave and outputs it as a received signal, and is used for the transmission signal and later-described sampling A synchronization detection unit that detects synchronization of a signal having a second frequency and outputs a synchronization detection signal; and synchronization of the reception signal and a signal having the second frequency with the synchronization detection signal as a trigger for starting sampling. includes but a sampling unit for outputting a sampled value sequence by sampling said received signal by said second frequency to be detected, and a distance calculator for calculating a distance to the obstacle on the basis of the sample value string The first frequency and the second frequency, characterized in that one frequency is a frequency which is synchronized with every cycle with respect to the other frequency.
In this obstacle detection device, the signal having the second frequency is preferably obtained by shifting the frequency of the transmission signal.
In this obstacle detection apparatus, it is preferable that the synchronization detection unit is configured using a flip-flop, and a transmission signal and a signal having a second frequency are input to the data terminal and the clock terminal of the flip-flop, respectively.
In this obstacle detection device, it is preferable that the synchronization detection unit detects synchronization by processing data obtained by digitizing a signal having the first and second frequencies by an AD converter by software.
In this obstacle detection apparatus, it is preferable that the synchronization detection unit detects synchronization using an output from a comparator that receives signals having the first and second frequencies.
In this obstacle detection device, it is preferable that one or both of the first and second frequencies are variable.
According to the obstacle detection device of the present invention, it is possible to detect an obstacle by accurately calculating the distance to the obstacle using signal waves such as light, radio waves, and ultrasonic waves with a low-cost and simple configuration. it can.
The block block diagram of the obstruction detection apparatus which concerns on the 1st Embodiment of this invention. (A)-(e) is a timing chart for demonstrating operation | movement of the apparatus. The block block diagram which shows the modification of the apparatus. The block block diagram of the obstruction detection apparatus which concerns on 2nd Embodiment. (A) (b) (c) is a timing chart for demonstrating operation | movement of the apparatus. The block block diagram which shows the modification of the apparatus. The block block diagram which shows the other modification of the apparatus. The block block diagram of the obstruction detection apparatus which concerns on 3rd Embodiment. The block block diagram which shows the modification of the apparatus. The block block diagram of the obstruction detection apparatus which concerns on 4th Embodiment. (A) (b) (c) is a timing chart for demonstrating operation | movement of the apparatus. The block block diagram of the obstruction detection apparatus which concerns on 5th Embodiment. (A) (b) (c) is a timing chart for demonstrating operation | movement of the apparatus. The block block diagram of the obstruction detection apparatus which concerns on 6th Embodiment. (A)-(d) is a timing chart for demonstrating operation | movement of the apparatus. The block block diagram of the general time difference detection part in the conventional obstacle detection apparatus. (A)-(d) is a timing chart for demonstrating operation | movement of the apparatus.
Hereinafter, an obstacle detection device according to an embodiment of the present invention will be described with reference to the drawings. Note that the transmission signal and the reception signal shown in FIGS. 2A and 2B are appropriately referred to as common contents in the following embodiments.
1 and 2 show the first embodiment. As illustrated in FIG. 1, the obstacle detection device 1 according to the present embodiment includes a first frequency generation unit 11 that generates a transmission signal having a first frequency, and a transmission signal from the first frequency generation unit 11. A signal wave is generated by amplitude-modulating a predetermined carrier wave, and a transmission unit 12 that transmits the signal wave to space, and a reception unit 13 that receives a reflected wave from an obstacle of the signal wave and outputs it as a reception signal. A second frequency generation unit 14 that generates a signal having a second frequency, and a first mixing unit 15 that mixes a transmission signal and a signal having the second frequency to output an intermediate frequency signal; The received signal and the signal having the second frequency are mixed with each other to output an intermediate frequency signal, and the two intermediate frequencies output from the first and second mixing units 15 and 16. Based on signal It includes a distance calculator 17 for calculating the distance to the obstacle, the.
The operation of the obstacle detection device 1 will be described with reference to FIG. 2 in addition to FIG. 2 (a) to 2 (e) are output from the first frequency generation unit 11, the reception unit 13, the first and second mixing units 15 and 16, and the distance calculation unit 17 in FIG. It is an example of the signal to be performed. As shown in FIGS. 2A and 2B, the transmission signal is a sine wave having the first frequency f1 = 1 / T, and the reception signal is received by the reception unit 13 after a lapse of time t from the transmission start of the transmission signal. It is output from. As shown in FIGS. 2C and 2D, the transmission signal and the reception signal are mixed with a sine wave having a second frequency f2 (where f1 ≠ f2) and passed through a low-pass filter. , A signal (intermediate frequency signal) having a frequency of difference | f1−f2 | and having a lower frequency. | * | Indicates the absolute value of *.
The mutual phase relationship between the transmission signal and the reception signal is also preserved in the transmission signal and the reception signal that have been converted to the intermediate frequency signal by mixing. Therefore, the phase difference between the transmission signal and the reception signal after mixing, more generally, the time difference tm between the two intermediate frequency signals and the period Tm of the transmission signal after mixing are expressed as follows. / T = tm / Tm. Paying attention to the time difference tm, tm = t × (Tm / T) = t × (f1 / fm), f1 = 1 / T, and fm = | f1-f2 | = 1 / Tm. That is, for example, if the frequency is converted to 1/10000 (fm = f1 / 10000), it is equivalent to extending the time t by 10,000 times (tm = t × 10000).
Therefore, the distance calculation unit 17 uses a sawtooth-shaped waveform voltage-time conversion process as described in the conventional example, or performs a process of counting the number of sampling pulses, and calculates the time difference tm. It can measure with high accuracy. Then, using the measured value (tau) of this time difference tm and the coefficient k for converting the measured value τ to the actual measured value (measured value of time t), the distance L to the obstacle is L = k × τ × c / 2. Here, c is a propagation speed of a transmission wave (radio wave, light, ultrasonic wave, etc.), and c≈3 × 10 8 m when the transmission wave is radio wave or light. The coefficient k is k = 1/10000 when tm = t × 10000 described above. When measuring the time difference tm, the distance calculation unit 17 detects, for example, the rising point of each signal and measures the time difference between the two rising points in FIG. Thus, the measurement value τ can be easily obtained with high accuracy by using the method of measuring the time difference between the two zero cross points. The distance calculation unit 17 measures the time difference tm in this way, and outputs information such as the distance L and the measured value τ corresponding to the distance L.
As described above, the obstacle detection apparatus 1 uses an amplitude-modulated continuous wave (AM-CW) based on a transmission signal as a signal wave, and a time difference (time of flight) between the transmission signal and a reception signal based on a reflected wave of the signal wave. Alternatively, it is a device that detects the obstacle by obtaining the distance to the obstacle that is the reflecting object by measuring the phase difference and recognizing the distance. The obstacle detection device 1 is characterized by converting both a transmission signal and a reception signal into an intermediate frequency when obtaining a time difference or a phase difference. According to the present embodiment, light, radio waves, ultrasonic waves, etc. can be obtained by a simple configuration in which both a transmission signal and a reception signal are converted to an intermediate frequency, and by a low-cost configuration without using an expensive high-frequency compatible circuit configuration. The distance to the obstacle can be obtained with high accuracy using the signal wave, and the obstacle can be detected by measuring the distance. In the case of the phase difference, it is necessary to consider uncertainty corresponding to an integer multiple of 2π radians.
FIG. 3 shows a modification of the first embodiment described above. The obstacle detection apparatus 1 includes a frequency shift unit 2 instead of the second frequency generation unit 14 in FIG. 1 of the first embodiment. The frequency shift unit 2 generates a signal having the second frequency used in the first and second mixing units 15 and 16 by shifting the frequency of the transmission signal generated by the first frequency generation unit 11. According to this modification, only one frequency generation unit may be provided as the first frequency generation unit 11 for transmission signal generation, and when the frequency generation unit is expensive, cost reduction can be expected. In addition, it replaces with the 1st frequency generation part 11 in the said FIG. 1, The frequency shift part 2 is provided, and the frequency of the signal with the 2nd frequency from the 2nd frequency generation part 14 is shifted by the frequency shift part 2. Thus, a transmission signal may be generated.
One or both of the first and second frequencies of the signal generated by the first and second frequency generators 11 and 14 in FIG. 1 of the first embodiment may be variable. Further, either one or both of the signals generated by the first frequency generation unit 11 and the frequency shift unit 2 in FIG. 3 may be variable. For example, the detection result can be output earlier as the first frequency f1 is higher than the second frequency f2. Further, the lower the first frequency f1 and the closer to the second frequency f2, the higher the distance resolution and the more accurate distance measurement becomes possible. In general, by changing the frequency in this manner, the larger the difference fm = | f1-f2 | between the first frequency f1 and the second frequency f2, the shorter Tm and thus the tm becomes shorter, and the time difference tm becomes larger. It can be measured in a short time. Conversely, the smaller the difference fm, the longer the tm and the more accurately the time difference tm can be measured. Therefore, the frequencies f1 and f2 are changed semi-fixed or dynamically according to the situation in which the obstacle detection apparatus 1 is applied, that is, depending on the choices such as priority on detection speed or priority on measurement accuracy. Thus, an appropriate operation can be realized. The configuration in which either or both of the frequencies f1 and f2 are variable can be similarly applied to the other embodiments described below, and the same effects as those of the modification shown here can be obtained.
4 and 5 show the second embodiment. As shown in FIG. 4, the obstacle detection apparatus 1 of the present embodiment amplitude-modulates a predetermined carrier wave with a first frequency generation unit 11 that generates a transmission signal having a first frequency and the transmission signal. Generates a signal wave and transmits the signal wave to space, a reception unit 13 that receives a reflected wave from an obstacle of the signal wave and outputs it as a reception signal, and a signal having a second frequency A sampling unit 3 that samples the transmission signal and the reception signal at the second frequency and outputs two sample value sequences, and two output by the sampling unit 3. A distance calculator 17 for calculating the distance to the obstacle based on the sample value sequence.
The operation of the obstacle detection apparatus 1 will be described with reference to FIG. 5 in addition to FIG. Each signal shown in FIGS. 5A, 5B, and 5C is an example of a signal that is output from each of the first frequency generation unit 11, the second frequency generation unit 14, and the sampling unit 3 in FIG. . As shown in FIG. 5A, the transmission signal is a sine wave having a first frequency (f1 = 1 / T). The reception signal is a sine wave having the same frequency f1 as that of the transmission signal, and is output from the reception unit 13 after a time difference t from the start of transmission of the transmission signal (see FIGS. 2A and 2B of the first embodiment). As shown in FIG. 5B, the signal output from the second frequency generation unit 14 is a signal whose sampling timing advances by a time difference Δts with respect to the frequency f1 of the received signal (frequency f2 = 1 / T2). ). That is, Δts = T2-T = 1 / f2-1 / f1. The second frequency generation unit 14 only needs to output a timing pulse for sampling.
When the transmission signal is sampled by the signal of the frequency f2 as described above, a sampling output (sample value string) as shown in FIG. 5C is obtained. This sample value sequence corresponds to the intermediate frequency obtained by mixing the transmission signal and the sine wave of frequency f2 shown in the first embodiment. Further, by sampling the received signal with a signal wave having the frequency f2, a sample value sequence corresponding to an intermediate frequency obtained by mixing the received signal and the sine wave having the frequency f2 is obtained. Therefore, by measuring the time lag between the two sample value sequences output by the sampling unit 3 (corresponding to the time difference tm in the first embodiment), based on the measured value, that is, in the first embodiment. The distance L to the obstacle can be obtained based on the measured value τ and the coefficient k. However, in the present embodiment, the distance L to the obstacle can be obtained using the number n of sampling signals at the time difference tm and the time difference Δts instead of the measurement value τ and the coefficient k.
For example, when a method using a phase difference is used as a method for obtaining the measurement value τ, if a result that the phase difference corresponds to n sampling signals is obtained, τ = Δts × n, and the distance L is L = c × τ / 2 = c × Δts × n / 2. The distance error ΔL (maximum error) based on this method is, for example, f 1 = 2.5015625 MHz, f 2 = 2.5 MHz, and when the signal wave is a radio wave (c≈3.0 × 10 8 m), ΔL = c × Δts / 2 = (1 / f2-1 / f1) × c / 2 = 3.75 cm (= 0.25 ns). Also, when obtaining the same phase point in each sample value sequence, a curve obtained by fitting each sample sequence is used, or a proportional distribution point between two points sandwiching the zero cross point is used for quantization. The error can be reduced. Further, the phase difference may be obtained from the cross-correlation function of the two sample value sequences. In this case, since a global determination can be made, the phase difference can be obtained more accurately without being influenced by local signal fluctuations. Further, the position of phase zero and the position of phase π in each sample value sequence can be detected by, for example, changing the sign of two adjacent sample values or increasing / decreasing from zero.
Further, when setting the two frequencies f1 and f2, by selecting a frequency in which one frequency is accurately synchronized with the other frequency every certain period, a specific “ The number n can be easily obtained by detecting the synchronized signal. That is, a state in which a transmission signal having a frequency f1 and a signal having a second frequency f2 have a specific phase value arbitrarily set at a certain moment is defined as a “synchronization” state, and the time is defined as a synchronization time. To do. For example, if a phase value of zero in a sine wave is set as a specific phase value of both signals, the state in which the waveforms of both signals rise simultaneously is the “synchronized” state, and the time is the synchronization time. Therefore, the synchronization between the signal having the second frequency f2 and the transmission signal is detected, and then the first synchronization between the signal having the second frequency f2 and the reception signal is subsequently detected as in the case of the transmission signal. To do. That is, the sampling points in the “synchronized” state are detected one by one in each of the two sample value sequences. The number n is set to 0 at the synchronization point detected for the transmission signal, and then the number n is added for each sampling point (sampling signal), and the final number n is obtained at the synchronization point detected for the reception signal. To do. This number n corresponds to the phase difference between the transmission signal and the reception signal. According to the present embodiment, the first and second mixing units 15 and 16 in the first embodiment are not necessary, and cost reduction can be expected due to the balance with the cost of the sampling unit 3.
(Two modifications of the second embodiment)
6 and 7 show a modification of the second embodiment. The modification of FIG. 6 includes a frequency shift unit 2 instead of the second frequency generation unit 14 in FIG. 4 of the second embodiment. The operation and effect of the obstacle detection apparatus 1 configured as described above are the same as the contents described in the modification (FIG. 3) in the first embodiment. That is, since this modification does not include the second frequency generation unit, if the second frequency generation unit 14 (pulse generation unit) is expensive, cost reduction can be expected. In the modification of FIG. 7, the sampling unit 3 in the second embodiment is configured using an AD converter (ADC).
8 and 9 show the fourth embodiment and its modification. As shown in FIG. 8, the obstacle detection apparatus 1 of the present embodiment amplitude-modulates a predetermined carrier wave by a first frequency generation unit 11 that generates a transmission signal having a first frequency and the transmission signal. Generates a signal wave and transmits the signal wave to space, a reception unit 13 that receives a reflected wave from an obstacle of the signal wave and outputs it as a reception signal, and has a second frequency A second frequency generation unit 14 that generates a signal, a synchronization detection unit 5 that detects synchronization between the transmission signal and a signal having the second frequency and outputs a synchronization detection signal, and starts sampling the synchronization detection signal. A sampling unit 3 that samples the received signal at the second frequency and outputs a sample value sequence until a synchronization between the received signal and the signal having the second frequency is detected as a trigger, and a fault based on the sample value sequence Distance calculator for calculating the distance to an object It is provided with a 7, a.
The obstacle detection device 1 of the present embodiment includes a sampling unit 3 and a synchronization detection unit 5 instead of the sampling unit 3 in the second embodiment (FIG. 4). The sampling unit 3 of the second embodiment samples both the transmission signal and the reception signal at the second frequency and outputs two sample value sequences. The sampling unit 3 of the present embodiment is a synchronization detection unit. In combination with 5, only the received signal is sampled and one sample value string is output. The synchronization detection signal output by the synchronization detection unit 5 is information corresponding to the sample value sequence of the transmission signal. Therefore, the sampling unit 3 samples (samples) the received signal using the synchronization detection signal from the synchronization detection unit 5 as a trigger, and sequentially adds the number n of the sampling points, as in the second embodiment. The final number n is obtained at the synchronization point detected for the received signal, and the number n is output to the distance calculator 17. The distance calculation unit 17 obtains the distance L by L = c × Δts × n / 2 as in the second embodiment.
As in this embodiment, in the method of starting sampling after synchronization detection, the received waveform can be easily averaged before sampling, and the distance measurement accuracy can be further improved by averaging. For example, in the case of averaging twice, the waveform of the received signal for a predetermined time (predetermined time interval exceeding the phase difference) after the synchronization detection by the first synchronization detection unit 5 is stored in a storage unit such as a RAM and synchronized. After the second synchronization detection by the detection unit 5, an averaging process is performed in which the waveform of the reception signal stored in the storage unit and the current waveform are added and divided by 2. Thereafter, the sampling unit 3 can perform sampling and synchronization detection of the averaged waveform, and obtain the number n corresponding to the phase difference.
The modification of FIG. 9 includes a frequency shift unit 2 instead of the second frequency generation unit 14 in FIG. The frequency shift unit 2 generates a signal having the second frequency used in the synchronization detection unit 5 and the sampling unit 3 by shifting the frequency of the transmission signal generated by the first frequency generation unit 11. According to this modification, only one frequency generation unit may be provided as the first frequency generation unit 11 for generating a transmission signal. If the frequency generation unit is expensive, cost reduction can be expected. In addition, it replaces with the 1st frequency generation part 11 in the said FIG. 8, and the frequency shift part 2 is provided, By the frequency shift part 2, the frequency of the signal with the 2nd frequency from the 2nd frequency generation part 14 is provided. The transmission signal may be generated by shifting.
10 and 11 show the fourth embodiment. As shown in FIG. 10, the obstacle detection device 1 of the present embodiment is configured by using the flip-flop 6 for the synchronization detection unit 5 in the third embodiment (FIG. 8). When a D-type flip-flop is used as the flip-flop 6, the input state of the data terminal D is output from the terminal Q when the signal input to the clock terminal C changes from L to H. Therefore, a signal having a first frequency from the first frequency generation unit 11, that is, a transmission signal is input to the data terminal D of the flip-flop 6, and a second frequency from the second frequency generation unit 14 is input to the clock terminal C. Input a signal with. Then, as shown in FIGS. 11A, 11B, and 11C, the flip-flop 6 “synchronizes the transmission signal and the signal having the second frequency in the phase zero state as in the third embodiment. ”Is detected and a synchronization detection signal is output from the terminal Q toward the sampling unit 3. The synchronous output in FIG. 11C is a binarized output of the terminal Q. The signal having the second frequency input to the clock terminal C has a certain DC offset so that the flip-flop 6 can properly recognize the L and H of the signal.
12 and 13 show the fifth embodiment. As shown in FIG. 12, the obstacle detection device 1 of the present embodiment includes an AD converter 4 in front of the synchronization detection unit 5 in the third embodiment (FIG. 8). The AD converter 4 receives a signal having a first frequency (that is, a transmission signal) and a signal having a second frequency from the first and second frequency generators 11 and 14, digitizes these signals, The digitized data is output to the synchronization detector 5. The synchronization detection unit 5 processes the data from the AD converter 4 by software, so that the transmission signal and the signal having the second frequency of the signal having the second frequency are processed, for example, in the state of zero phase, as in the third embodiment. “Synchronization” is detected and a synchronization detection signal is output to the sampling unit 3.
As shown in FIGS. 13A and 13B, the AD converter 4 performs sampling processing, that is, digitization processing on the signal from the first frequency generation unit 11 according to the timing of the signal from the second frequency generation unit 14. . As shown in FIGS. 13A, 13B, and 13C, the synchronization detection unit 5 detects the phase coincidence point between the signals of both frequencies, and outputs a synchronization detection signal when it is detected. When flip-flops are used as in the fourth embodiment, they are affected by temperature and power supply voltage fluctuations. However, when the AD converter 4 is used as in this embodiment, those effects are minor and more reliable. Highly reliable synchronization detection.
14 and 15 show the sixth embodiment. As shown in FIG. 14, the obstacle detection device 1 of the present embodiment receives a signal having the first and second frequencies in the previous stage of the synchronization detection unit 5 in the third embodiment (FIG. 8). The synchronization detection unit 5 includes a comparator 7, and “synchronization” of the signal having the transmission signal and the second frequency using the output from the comparator 7 in the same manner as in the third embodiment, for example, in a phase zero state. And outputs a synchronization detection signal toward the sampling unit 3. The comparator 7 is an IC that outputs a result obtained by comparing two input values. If the amplitude value of the signal input to the plus terminal is larger than the signal input to the minus terminal, the output is H, and if it is smaller, the output is L. Therefore, a signal having a first frequency (that is, a transmission signal) from the first frequency generation unit 11 is input to the plus terminal of the comparator 7, and a signal from the second frequency generation unit 14 is input to the minus terminal of the comparator 7. input. Since the output is indefinite when the signal level is the same level, an offset voltage is provided in advance on the minus terminal side.
As a result, as shown in FIGS. 15A and 15B, a comparator output is obtained for the transmission signal and the signal having the second frequency, as shown in FIG. 15C (FIG. 15B). The broken line in is a reference waveform). As shown in FIG. 15D, the synchronization detection unit 5 detects “synchronization” by sampling the comparator output according to the timing of the signal from the second frequency generation unit 14, and synchronizes toward the sampling unit 3. A detection signal is output. Depending on how the offset voltage is set, the output of the comparator 7 becomes H at the next sampling of the phase matching point between the first frequency and the second frequency. Therefore, it is necessary to convert the distance calculated in the distance calculation unit 17. Further, as described above, when the synchronization detection unit 5 takes in the output of the comparator 7 at the timing of the second frequency, the output changes from L to H at the point where the phases of the respective frequencies coincide with each other. The synchronization detection signal may be output at this timing.
The present invention is not limited to the above-described configuration, and various modifications can be made. For example, it can be set as the structure which mutually combined the structure of each embodiment mentioned above and those modifications. In the above embodiment, the signal wave is generated by amplitude-modulating a predetermined carrier wave with the transmission signal. However, the transmission signal (that is, the output signal from the first frequency generation unit 11) is used without using the carrier wave. You may make it transmit itself to space as a signal wave.
DESCRIPTION OF SYMBOLS 1 Obstacle detection apparatus 2 Frequency shift part 3 Sampling part 4 AD converter 5 Synchronization detection part 6 Flip-flop 7 Comparator 11 1st frequency generation part 12 Transmission part 13 Reception part 14 2nd frequency generation part 15 1st mixing part 16 Second mixing unit 17 Distance calculation unit
In an obstacle detection device that detects an obstacle using a signal wave propagating in space,
A transmitter that generates a signal wave by amplitude-modulating a predetermined carrier wave with a transmission signal having a first frequency and transmits the signal wave to space;
A receiving unit that receives a reflected wave from the obstacle of the signal wave and outputs it as a received signal;
A synchronization detection unit that detects synchronization between the transmission signal and a signal having a second frequency used for sampling and outputs a synchronization detection signal;
Using the synchronization detection signal as a trigger for starting sampling, the received signal is sampled at the second frequency until the synchronization between the received signal and the signal having the second frequency is detected, and a sample value sequence is output. A sampling unit to perform,
A distance calculator that calculates the distance to the obstacle based on the sample value sequence,
The obstacle detection device according to claim 1, wherein the first frequency and the second frequency are frequencies at which one frequency is synchronized with the other frequency every certain period.
It said second signal having a frequency, an obstacle detection device according to claim 1, characterized in that obtained by shifting the frequency of the transmission signal.
The synchronization detection unit is configured with a flip-flop, according to claim 1 or claim, characterized by inputting a signal having the transmitting signal and the second frequency to the data terminal and the clock terminal of the flip-flop Item 3. The obstacle detection device according to Item 2 .
The synchronization detection unit, the transmission signal and claim 1 or claim 2 a second signal having a frequency and detecting said sync by the data digitized by the AD converter for processing by software Obstacle detection device according to.
The synchronization detection unit barrier of claim 1 or claim 2, wherein the detecting the synchronization using the output from the comparator which receives the signal having the transmission signal and the second frequency Detection device.
Obstacle detection device according to any one of claims 1 to 5, wherein the first frequency is variable.
Obstacle detection device according to any one of claims 1 to 5, wherein the second frequency is variable.
Obstacle detection device according to any one of claims 1 to 5, wherein the first and second frequency is variable.
JP2010066238A 2010-03-23 2010-03-23 Obstacle detection device Expired - Fee Related JP5654253B2 (en)
JP2010066238A JP5654253B2 (en) 2010-03-23 2010-03-23 Obstacle detection device
JP2011196924A JP2011196924A (en) 2011-10-06
JP5654253B2 true JP5654253B2 (en) 2015-01-14
ID=44875325
JP2010066238A Expired - Fee Related JP5654253B2 (en) 2010-03-23 2010-03-23 Obstacle detection device
JP (1) JP5654253B2 (en)
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