Source: http://www.google.com/patents/US20030128081?ie=ISO-8859-1&dq=6,064,942
Timestamp: 2014-03-15 03:02:26
Document Index: 549239562

Matched Legal Cases: ['art 204', 'art 206', 'art 204', 'art 206', 'art 206', 'art 204', 'art 206', 'art 206', 'art 204', 'art 204', 'art 206', 'art 204', 'art 206']

Patent US20030128081 - Bulk acoustic wave resonator with two piezoelectric layers as balun in ... - Google PatentsSearch Images Maps Play YouTube News Gmail Drive More »Sign inAdvanced Patent SearchPatentsA bulk acoustic wave device having two resonators in a stacked-up configuration separated by a dielectric layer. The device can be coupled to a lattice filter or a ladder filter to form a passband filter with an unbalanced input port and two balanced output ports. One or more such passband filters can...http://www.google.com/patents/US20030128081?utm_source=gb-gplus-sharePatent US20030128081 - Bulk acoustic wave resonator with two piezoelectric layers as balun in filters and duplexersAdvanced Patent SearchPublication numberUS20030128081 A1Publication typeApplicationApplication numberUS 10/045,645Publication dateJul 10, 2003Filing dateJan 9, 2002Priority dateJan 9, 2002Also published asCN1695298A, CN100488044C, DE60329654D1, EP1464115A2, EP1464115A4, EP1464115B1, US6670866, WO2003058809A2, WO2003058809A3, WO2003058809A8, WO2003058809B1Publication number045645, 10045645, US 2003/0128081 A1, US 2003/128081 A1, US 20030128081 A1, US 20030128081A1, US 2003128081 A1, US 2003128081A1, US-A1-20030128081, US-A1-2003128081, US2003/0128081A1, US2003/128081A1, US20030128081 A1, US20030128081A1, US2003128081 A1, US2003128081A1InventorsRobert Aigner, Juha EllaOriginal AssigneeNokia CorporationExport CitationBiBTeX, EndNote, RefManReferenced by (48), Classifications (16), Legal Events (8) External Links: USPTO, USPTO Assignment, EspacenetBulk acoustic wave resonator with two piezoelectric layers as balun in filters and duplexersUS 20030128081 A1Abstract A bulk acoustic wave device having two resonators in a stacked-up configuration separated by a dielectric layer. The device can be coupled to a lattice filter or a ladder filter to form a passband filter with an unbalanced input port and two balanced output ports. One or more such passband filters can be used, together with another lattice or ladder filter, to form a duplexer having an unbalanced antenna port, two balanced ports for one transceiver part and two balanced ports for another transceiver part. Images(21) Claims(56)
BEST MODE TO CARRY OUT THE PRESENT INVENTION [0163]FIG. 4 is a diagrammatic representation of the balun 10, according to the present invention. The balun 10 comprises a bulk acoustic wave device 20 coupled to a device ground 12, a signal input end 14 and two signal output ends 16, 18. The single input end 14 is an unbalanced port, whereas the two signal output ends 16, 18 are balanced ports. The bulk acoustic wave device 20, as shown in FIG. 5, has two resonators and a dielectric layer therebetween. As shown, the device 20 is formed on a substrate 30 and comprises a first electrode 40, a first piezoelectric layer 42, a second electrode 44 connected to the device ground 12, a third electrode 60, a dielectric layer 50 between the second electrode 44 and the third electrode 60, a second piezoelectric layer 62 and a fourth electrode 64. The first electrode 40, the first piezoelectric layer 42 and the second electrode 44 have an overlapping area for forming a first resonator 92. The third electrode 60, the second piezoelectric layer 62 and the fourth electrode 64 have an overlapping area for forming a second resonator 94. The bulk acoustic wave device 20 has a resonant frequency and an acoustic wavelength, λ, characteristic of the resonant frequency. The thickness of the first and second piezoelectric layers 42, 46 is substantially equal to λ/2. It is preferable to have an acoustic mirror 34 formed between the first electrode 40 and the substrate 30 to reflect acoustic waves back to the first resonator 92. As shown in FIG. 5, an opening 52 is provided in the first piezoelectric layer 42 and the dielectric layer 50 so that a section of the first electrode 40 is exposed for use as a connection point 41 to the signal input end 14 of the balun 10. Similarly, an opening 51 is provided in the dielectric layer 50 so that a section of the second electrode 44 is exposed for use as a connection point 45 to the device ground 12. The first resonator 92 and the second resonator 94 have an overlapping area 70, defining an active area of the bulk acoustic wave device 20. [0164] As can be seen from the cross-sectional view of the two-piezoelectric layer structure of FIG. 5, there will probably be unequal parasitics from the first signal output end 16 and the second signal output end 18 to the ground electrode 44. These unequal parasitics may cause amplitude and phase imbalance between the balanced ports. The unequal parasitics can be improved by using a compensation capacitor 72 between the fourth electrode 64 and the ground electrode 44, as shown in FIG. 6. It should be noted that the first electrode 40 is used as a signal input port so that the ground electrode 44 provides electrical isolation between the input and output. Furthermore, the dielectric layer 50 is used to electrically decouple the lower output port, which is the third electrode 60. The dielectric layer 50 can be any thickness. A thicker dielectric layer reduces the parasitic coupling between the ground electrode 44 and the upper electrodes 60, 64, but it also increases acoustic losses. Thus, a good starting value of the dielectric layer thickness for optimizing performance is λ/2. Preferably, the dielectric layer 50 has a low dielectric constant to minimize the acoustic losses. The thickness and material of the dielectric layer can also be optimized in a way that the temperature coefficient of the whole device is substantially reduced. Silicon Oxide is known to have such a compensating effect when using the right thickness. Thus, it is advantageous to use a material with a positive temperature coefficient, such as silicon oxide, with a proper thickness as the dielectric layer 50 to compensate the negative overall temperature coefficients of the other layers. In order to widen the bandwidth in this dual-cavity resonator 20, it is possible to couple inductance elements 74, 76 in a shunt of either or both resonators 92, 94. In general, the inductance values for 1 GHz frequencies are small. Thus, it is possible to implement the inductance elements 74, 76 as spiral coils on a chip, for example. [0165] The compensation capacitance is provided so that the capacitance from the first signal output end 16 to ground is equal to that from the second signal output end 18 to ground. One way to provide the compensation capacitance is to clear the second piezoelectric layer 62 outside the active area 70 of the bulk acoustic wave device 20, so that the extended section 46 of the ground electrode 44 and the extended section 66 of the fourth electrode 64 overlap each other over an area 67. [0166] As shown in FIGS. 5 and 6, the unbalanced resonator 92 is at the bottom of the dual-cavity structure. It is also possible that the unbalanced resonator may be at the top of the structure. However, the latter structure would generate unequal parasitics to the substrate from the two balanced ports. [0167] For applications with lower bandwidth requirements, another embodiment of the present invention, as shown in FIG. 7 can be used. As shown in FIG. 7, the balun 10 has two identical stacks 21, 21′ of layers, similar to the bulk acoustic wave device 20 of FIGS. 5 and 6. However, the first electrode 40′ and the third electrode 60′ of the layer stack 21′, and the second electrode 44 and the third electrode 60 of the layer stack 20 are connected to ground 12. In addition, the second electrode 44′ of the layer stack 211′ is connected to the first electrode 40 of the layer stack 21 and is used as the signal input end 14. The top electrode 64 of the layer stack 21 is used as the first signal output end 16, while the top electrode 64′ of the layer stack 21′ is used as the second signal output end 18. Functionally, this double-structure is equivalent to the balun 10, as shown in FIGS. 4-6. With the double-structure, there is no need for the compensation capacitance because the electrodes 60, 60′ below the upper piezoelectric layers 62, 62′ are grounded. This electric shielding effect results in the symmetric impedance for the first and second signal output ends 16, 18. The parasitic capacitance of the dielectric layers 50, 50′ is parallel to the signal input end 14. This parasitic capacitance somewhat degrades the bandwidth of the device but does not harm its symmetry. The cross-connected input electrodes 40, 44′ generate a perfect 180� phase between the acoustic waves in the stack 21 and the stack 21′. Matching and bandwidth widening coils, similar to inductance elements 74, 76, as shown in FIG. 6, can also be implemented on the double-structure 10. The structure, as shown in FIG. 7, also has a potential benefit if the impedance level at the outputs is significantly larger than the impedance at the input. Without further matching elements, the differential impedance at the output is larger than the single-ended input impedance by a factor ≧4. [0168] The balun 10, as shown in FIGS. 4-7, can be used as part of a filter that has one unbalanced port and two balanced ports. For example, the balun 10 can be coupled to a ladder filter 120 having one or more L-segments to form a passband filter 100, as shown in FIG. 8. The balun 10 can also be coupled to a lattice filter 150 having one or more cross-connection segments to form a passband filter 100′, as shown in FIG. 9. The unbalance port is denoted by reference numeral 102, and the balanced ports are denoted by reference numerals 104 and 106. These passband filters 100, 100′ can be combined with each other or with other ladder or filter segments to form a duplexer or a dual-channel passband filter, as shown in FIGS. 10-13. In FIGS. 8-13, the balun 10 or 10′ is represented by one resonator 92 coupled between a signal input end 14 and a device ground 12, and one resonator 94 coupled between two signal output ends 14, 16. It is understood that either the BAW device of a single structure, as shown in FIGS. 5 and 6, or that of the double structure, as shown in FIG. 7, can be used for the balun 10 or 10′ in the filters in FIGS. 8-13. [0169] In the filter 100, as shown in FIG. 8, the balun 10 is combined with the ladder filter 120, which is coupled between the unbalanced port 102 of the passband filter 100 and the signal input end 14 of the balun 10. The two signal output ends 16, 18 of the balun 10 are connected to the balanced ports 104, 106. The ladder filter 120, as shown in FIG. 8, has only one L-segment including one series element 130 and one shunt element 140. However, the ladder filter 120 can have two or more L-segments. As shown in FIG. 8, the series element 130 has a first end 132 connected to the signal input end 14 of the balun 10, and a second end 134 connected to the unbalanced port 102. The shunt element 140 has a first end 142 connected to the second end 134 of the series element 130 and a second end 144 connected to the device ground. [0170] When the balun 10 is combined with the lattice filter 150, the signal input end 14 of the balun 10 is coupled to the unbalanced port 102, and the lattice filter 150 is coupled between the signal outputs 16, 18 of the balun 10 and the balanced ports 104, 106, as shown in FIG. 9. As shown in FIG. 9, the lattice filter 150 has only one cross-connecting segment including two series elements 160, 170 and two shunt elements 180, 190. However, the lattice filter 150 can have two or more such segments. The lattice filter 150 has a first filter end 151 having a first terminal 152 and a second terminal 153, separately coupled to the first and second signal output ends 16, 18 of the balun 10, and a second filter end 154 having a third terminal 155 and a fourth terminal 156 separately coupled to the balanced ports 104, 106 of the passband filter 100′. As shown in FIG. 9, the series element 160 has a first end 162 connected to the first terminal 152 and a second end 164 connected to the third terminal 155. The series element 170 has a first end 172 connected to the second terminal 153 and a second end 174 connected to the fourth terminal 156. The shunt element 180 has a first end 182 connected to the second end 164 of the series element 160, and a second end 184 connected to the first end 172 of the series element 170. The shunt element 190 has a first end 192 connected to the first end 162 of the series element 160, and a second end 194 connected to the second end 174 of the series element 170. [0171] The passband filters 100 and 100′, as shown in FIGS. 8 and 9, can be further combined to form a dual-channel passband filter or a duplexer, as shown in FIGS. 10-13. In FIGS. 10-13, each duplexer has two transceiver filters 204 and 206. For example, the filter 100′, as shown in FIG. 9 is used as a passband filter in the RX-part 204 of the duplexers 200, 201, 202 and 203, as shown in FIGS. 10-13. Each of these duplexers 200, 201, 202 and 203 has an antenna port 220 and two transceiver ports 210 and 230. The antenna port 210 is unbalanced, whereas each of the two transceiver ports 210, 230 has two balanced terminals. [0172] In the duplexer 200 as shown in FIG. 10, another lattice filter 150′ is used as a passband filter in the TX-part 206. In order to match the lattice filter 150 and the lattice filter 150′ two phase shifters 242 and 244 are used to couple between the second end 154 of the lattice filter 150 and the second end 154 of the lattice filter 150′. [0173] In the duplexer 201, as shown in FIG. 11, two similar passband filters are separately used in the RX-part 204 and TX-part 206. A phase shifter 242 is used for matching these two passband filters. [0174] In the duplexer 202, as shown in FIG. 12, a ladder filter 250 having two L-segments is used as the passband filter in the TX-part 206. As shown, the ladder filter 250 has a first end 252 connected to an unbalanced port 230, and a second end 254 coupled to the antenna port 220. A phase shifter 242 is used for matching the passband filter in the RX-part 204 and that in the TX-part 206. The ladder filter 250 has two series elements 260, 270 and two shunt elements 280, 290. The series element 260 has a first end 262 connected to the first end 252 of the ladder filter 250, and a second end 264. The series element 270 has a first end 272 connected to the second end 264 of the series element 260, and a second end 274 connected to the second end 254 of the ladder filter 250. The shunt element 280 has a first end 282 connected to the second end 264 of the series element 260, and a second end 284 connected to ground. The shunt element 290 has a first end 292 connected to the second end 274 of the series element 270, and a second end 294 connected to ground. [0175] In additional to the bulk acoustic wave components in the duplexer 202, another balun 10′ is used in the duplexer 203, as shown in FIG. 13. In the duplexer 203, the balun 10′ is used to transform the unbalanced port of the TX-part into a balanced port. As shown, the signal input end 14 of the balun 10′ is connected to the first end 252 of the lattice filter 250, and the signal output ends 16, 18 are connected to the balanced port 230. It should be noted that the lattice filter 250, as shown in FIGS. 12 and 13, has two L-segments. However, the lattice filter can have one L-segment or three or more L-segments. [0176] In the bulk acoustic wave structure as shown in FIGS. 5 to 7, the piezoelectric layers 42 and 62 have substantially the same thickness, or approximately 8/2. However, when the balun 10 is used in a duplexers 200-203, it is preferred that the thickness T1 the piezoelectric layer 42 of the first resonator 92 is slightly different from the thickness T2 the piezoelectric layer 62 of the second resonator 94. As shown in FIG. 14, T2 is slightly greater than T1. However, it is also possible that T2 is smaller than T1. As such, the piezoelectric layer in each of the shunt and series elements in the TX-part 206 of the duplexer has a thickness substantially equal to T2, whereas the piezoelectric layer in each of the shunt and series elements in the RX-part 204 has a thickness substantially equal to T1. As shown in FIG. 14, the single-layer resonator 24 represents a series or shunt element in the lattice or ladder filter in the RX-part and the single-layer resonator 26 represents a series or shunt element in the lattice or ladder filter in the TX-part of the duplexer. As shown, the piezoelectric layer 62 in the resonator 24 has a thickness substantially equal to T1, whereas the piezoelectric layer 42 in the resonator 26 has a thickness substantially equal to T2. [0177] Furthermore, the lattice filters 150, 150′ in FIGS. 9-13 may have unequal series and shunt resonator areas to improve close-in selectivity, as disclosed in EP 1017170 �A Balanced Filter Structure�. As shown in FIG. 15, the resonator area A1 of the series elements 160, 170 is slightly greater than the resonator area B1 of the shunt elements 180, 190. [0178] Moreover, in the duplexers 200, 201, 202, 203, as shown in FIGS. 10-13, the lattice filter 150 can be omitted such that the signal output ends 18, 16 of the balun 10 are directly connected to the balanced port 210. In the duplexer 201 as shown in FIG. 11, both lattice filters 150, 150′ can be omitted. In the duplexer 203 as shown in FIG. 13, both the lattice filter 150 and the ladder filter 250 can be omitted. As such, the duplexer will have one balun 10 in one transceiver part 204 and one filter 150, or 250 in another transceiver part 206, as shown in FIGS. 16a through 17 b. Alternatively, each of the transceiver parts will have a balun 10, 10′ as its filter, as shown in FIG. 18. [0179] The phase shifters 242, 244 in the duplexers 200, 201, 202 and 203 provide a 90� phase-shift to signals conveyed between the RX-part 204 and the TX-part 206. However, the phase shift angle can be smaller or greater than 90�. [0180] Thus, although the invention has been described with respect to a preferred embodiment thereof, it will be understood by those skilled in the art that the foregoing and various other changes, omissions and deviations in the form and detail thereof may be made without departing from the scope of this invention. Referenced byCiting PatentFiling datePublication dateApplicantTitleUS6911708 *Feb 19, 2004Jun 28, 2005Lg Electronics Inc.Duplexer filter having film bulk acoustic resonator and semiconductor package thereofUS6946928Oct 30, 2003Sep 20, 2005Agilent Technologies, Inc.Thin-film acoustically-coupled transformerUS6987433Apr 29, 2004Jan 17, 2006Agilent Technologies, Inc.Film acoustically-coupled transformer with reverse C-axis piezoelectric materialUS7019605Oct 30, 2003Mar 28, 2006Larson Iii John DStacked bulk acoustic resonator band-pass filter with controllable pass bandwidthUS7091649Apr 29, 2004Aug 15, 2006Avago Technologies Wireless Ip (Singapore) Pte. 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Ltd.BAW apparatusEP2509221A1 *Mar 29, 2012Oct 10, 2012Commissariat A L'energie Atomique Et Aux Energies AlternativesDevice using a resonator based filterWO2005039063A1 *Aug 13, 2004Apr 28, 2005Juha EllaeMimo and diversity front-end arrangements for multiband multimode communication enginesWO2005043751A1 *Oct 29, 2004May 12, 2005Agilent Technologies IncSolidly mounted stacked bulk acoustic resonatorWO2005043752A1 *Oct 29, 2004May 12, 2005Agilent Technologies IncFilm acoustically-coupled transformer with increased common mode rejectionWO2005043753A1 *Oct 29, 2004May 12, 2005Agilent Technologies IncPass bandwidth control in decoupled stacked bulk acoustic resonator devicesWO2005043756A1 *Oct 29, 2004May 12, 2005Agilent Technologies IncTemperature-compensated film bulk acoustic resonator (fbar) devicesWO2005046052A1 *Oct 29, 2004May 19, 2005Agilent Technologies IncImpedance transformation ratio control in film acoustically-coupled transformersWO2005046053A1 *Oct 29, 2004May 19, 2005Agilent Technologies IncFilm acoustically-coupled transformerWO2006039996A1 *Sep 23, 2005Apr 20, 2006Epcos AgCircuit working with acoustic volume waves and component connected to the circuitWO2014008918A1 *Jul 9, 2012Jan 16, 2014Telefonaktiebolaget L M Ericsson (Publ)Transceiver front-endWO2014008919A1 *Jul 9, 2012Jan 16, 2014Telefonaktiebolaget L M Ericsson (Publ)Transceiver front-endWO2014008921A1 *Jul 9, 2012Jan 16, 2014Telefonaktiebolaget L M Ericsson (Publ)Transceiver front-end* Cited by examinerClassifications U.S. Classification333/133, 333/187International ClassificationH03H9/00, H03H9/70, H03H7/42, H03H9/58, H03H9/54Cooperative ClassificationH03H9/706, H03H9/589, H03H7/42, H03H9/0095, H03H9/0571European ClassificationH03H9/05B3B, H03H9/70B1, H03H9/58F4C, H03H9/00U2Legal EventsDateCodeEventDescriptionMay 7, 2013ASAssignmentOwner name: AVAGO TECHNOLOGIES GENERAL IP (SINGAPORE) PTE. 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