Source: https://patents.google.com/patent/US8488655B2/en
Timestamp: 2019-10-20 10:07:57
Document Index: 516684815

Matched Legal Cases: ['Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61']

US8488655B2 - PHY layer parameters for body area network (BAN) devices - Google Patents
PHY layer parameters for body area network (BAN) devices Download PDF
US8488655B2
US8488655B2 US12/760,516 US76051610A US8488655B2 US 8488655 B2 US8488655 B2 US 8488655B2 US 76051610 A US76051610 A US 76051610A US 8488655 B2 US8488655 B2 US 8488655B2
US12/760,516
US20100260162A1 (en
2009-04-14 Priority to US16905409P priority Critical
2009-04-14 Priority to US16904809P priority
2010-04-14 Application filed by Texas Instruments Inc filed Critical Texas Instruments Inc
2010-04-20 Assigned to TEXAS INSTRUMENTS INCORPORATED reassignment TEXAS INSTRUMENTS INCORPORATED ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: SCHMIDL, TIMOTHY M., BATRA, ANUJ, HOSUR, SRINATH, ROH, JUNE CHUL
2010-10-14 Publication of US20100260162A1 publication Critical patent/US20100260162A1/en
2013-07-16 Publication of US8488655B2 publication Critical patent/US8488655B2/en
The present application claims priority to: U.S. Provisional Patent Application No. 61/169,048, filed on Apr. 14, 2009; U.S. Provisional Patent Application No. 61/169,054, filed on Apr. 14, 2009; U.S. Provisional Patent Application No. 61/170,764, filed on Apr. 20, 2009; U.S. Provisional Patent Application No. 61/172,559, filed on Apr. 24, 2009; U.S. Provisional Patent Application No. 61/172,889, filed on Apr. 27, 2009; U.S. Provisional Patent Application No. 61/300,312, filed on Feb. 1, 2010; U.S. Provisional Patent Application No. 61/306,663, filed on Feb. 22, 2010; U.S. Provisional Patent Application No. 61/313,440, filed on Mar. 12, 2010; U.S. Provisional Patent Application No. 61/318,076, filed on Mar. 26, 2010; and U.S. Provisional Patent Application No. 61/319,063, filed on Mar. 30, 2010; all of which are hereby incorporated herein by reference.
This application also may contain subject matter that relates to the following commonly assigned co-pending applications incorporated herein by reference: “PHY Layer Options For Body Area Network (BAN) Devices,” U.S. Ser. No. 12/760,510, filed Apr. 14, 2010; and “PHY Layer PPDU Construction For Body Area Network (BAN) Devices,” U.S. Ser. No. 12/760,513, filed Apr. 14, 2010.
FIG. 16 shows a block diagram of PLOP header construction in accordance with embodiments of the disclosure;
FIG. 17 shows a block diagram of an alternative PLOP header construction in accordance with embodiments of the disclosure;
FIG. 19 shows a spreading scheme in accordance with embodiments of the disclosure;
In FIG. 1, the PLCP header 104 is shown to be the second main component of the PPDU 100. The purpose of PLCP header 104 is to convey information about PHY and MAC parameters to aid in decoding the PSDU 106 at the receiver. In at least some embodiments, the PLCP header 106 comprises a PHY header field 112 (e.g., 15 bits in length), a header check sequence (HCS) field 114 (e.g., 4 bits in length), and a Bose, Ray-Chaudhuri, Hocquenghem (BCH) parity bits field (e.g., 12 bits in length). The BCH parity bits are added in order to improve the robustness of the PLOP header 104. The PHY header field 112 may further be decomposed into a RATE field 120 (e.g., 3 bits in length), a LENGTH field (e.g., 8 bits in length), a SCRAMBLER SEED field 128 (e.g., 1 bit in length), a BURST MODE field 130 (e.g., 1 bit in length), and reserved bit fields 122 and 126. The PLOP header 104 is transmitted using the given header data rate in the operating frequency band.
When transmitting the PPDU 100, the PLOP preamble 102 is sent first, followed by the PLOP header 104 and finally the PSDU 106. All multiple byte fields are transmitted with least significant byte first and each byte is transmitted with the least significant bit (LSB) first. In at least some embodiments, a compliant device is able to support transmission and reception in one of the following frequency bands: 402-405 MHz, 420-450 MHz, 863-870 MHz, 902-928 MHz, 950-956 MHz, 2360-2400 MHz and 2400-2483.5 MHz.
Various data-rate dependent parameters for each of these possible frequency bands of operation are provided herein and are intended to conform to established regulations, such as in the United States, Europe, Japan and Korea. FIGS. 2A-2G show tables with data-rate dependent parameter information for a PLOP header and a PSDU in accordance with embodiments of the disclosure. The data-rate dependent parameters in FIGS. 2A-2F include parameters such as modulation type, symbol rate (in ksps), code rate (k/n), spreading factor (S), bandwidth-bit duration (BT), pulse shape, information data rate (in kbps), and whether support for a set of parameters is mandatory or optional.
FIG. 16 shows a block diagram 1600 of PLOP header construction in accordance with embodiments of the disclosure. As shown, the block diagram 1600 comprises a concatenate block 1602 that receives a PHY header and HCS as input. A BCH encoder 1604 operates on the output of the concatenate block 1602, followed by a spreader 1606, a bit interleaver 1608, a scrambler 1610, and a symbol mapper 1612. In the PLOP header construction of block diagram 1600, the scrambler 1610 is located after the bit interleaver 1608 and before the symbol mapper 1612. In at least some embodiments, the scrambler 1610 corresponds to the scrambler 1018 shown for the PSDU construction block diagram 1000 of FIG. 10.
In the PLOP header construction of block diagram 1600, the scrambling operation (at symbol level) of the scrambler 1610 is applied to PLOP header and the initial seed for the scrambler 1610 is known a priori to the receiver. One possible method for pre-assigning the scrambler seed is to map the even channels to scrambler seed 0, and odd channels to scrambler seed 1, or vice versa. As an example, if devices are operating on channel 2 (an even channel), then scrambler seed 0 would be used to scramble the PLOP header. At the end of the PLOP header, the scrambler 1610 would be re-initialized with the scrambler seed specified by the MAC (either scrambler seed 0 or 1), and the re-initialized scrambler would be used to scramble the PSDU. If devices are operating on channel 3 (an odd channel), then scrambler seed 1 would be used to scrambler the PLOP header. Again, at the end of the PLOP header, the scrambler 1610 would be re-initialized with the scrambler seed specified by the MAC (either scrambler seed 0 or 1), and the re-initialized scrambler would be used to scramble the PSDU. Although only one method is shown for pre-assigning the scrambler seed for the PLOP header based on the channel information, there are many other ways to pre-assign the scrambler seed for the PLOP header.
FIG. 17 shows a block diagram 1700 of an alternative PLOP header construction in accordance with embodiments of the disclosure. The PLOP header construction components for block diagram 1700 are similar to the corresponding PLOP header construction components for block diagram 1600, except for the scrambler 1712. In the PLOP header construction of block diagram 1700, the scrambler 1712 is located after the symbol mapper 1710 and may correspond to scrambler 1420 for PSDU construction block diagram 1400.
the first rem(Nshorten,NCW) codewords will have Nspew+1 shortened bits (message bits that are set to 0), while the remaining codewords will have Nspew shortened bits. After encoding, the shortened bits are discarded prior to transmission (i.e., the shortened bits are never transmitted on-air).
r ⁡ ( x ) = ∑ i = 0 11 ⁢ ⁢ r i ⁢ x i = x 12 ⁢ m ⁡ ( x ) ⁢ mod ⁢ ⁢ g ⁡ ( x ) ,
and ri,i=0, . . . , 11. Further, mi,i=0, . . . , 50 are elements of GF (2). The message polynomial m(x) is created as follows: m50 is the first bit of the message and m0 is the last bit of the message, which may be a shortened bit. The order of the parity bits is as follows: r11 is the first parity bit transmitted, r10 is the second parity bit transmitted, and ro is the last parity bit transmitted.
FIG. 19 shows a spreading scheme 1900 in accordance with embodiments of the disclosure. As shown in spreading scheme 1900, for a spreading factor of 2, each input bit is repeated two times. For a spreading factor of 4, each input bit is repeated four times.
In the PSDU construction of block diagrams 1000 (FIG. 10) and 1400 (FIG. 14), the bits interleavers 1016 and 1416 perform bit interleaving as given below. The same or similar bit interleaving process also may be performed by the bit interleavers 1608 and 1708 of the respective PLOP construction block diagrams 1600 (FIG. 16) and 1700 (FIG. 17). Although not required, the bit interleavers 1016, 1416, 1608, and 1708 may represent a single bit interleaver.
b ⁡ ( i ) = a ⁡ [ S × rem ⁡ ( i , 2 ) + ⌊ i 2 ⌋ ] ⁢ ⁢ i = 0 , 1 , … ⁢ , 2 ⁢ S - 1.
In the PSDU construction of block diagrams 1000 (FIG. 10) and 1400 (FIG. 14), the symbol mappers 1020 and 1418 perform may perform GMSK symbol mapping. The same or similar GMSK symbol mapping also may be performed by the symbol mappers 1612 and 1710 of the respective PLOP construction block diagrams 1600 (FIG. 16) and 1700 (FIG. 17). Although not required, the symbols mappers 1020, 1418, 1612, and 1710 may represent a single bit interleaver.
For the D-PSK constellations, the coded potentially spread and interleaved bit stream is mapped onto one of three rotated and differentially-encoded constellations: π/2-DBPSK, π/4-DQPSK, or π/8-D8PSK. The encoded information is carried in the phase transitions between symbols. For the PLOP preamble to PLOP header transition, the phase change is relative to the last symbol for the PLOP preamble. For the PLOP header to PSDU transition, the phase change is relative to the last symbol for the PLOP header. The binary bit stream b(n), n=0, 1, . . . , N−1 is mapped onto a corresponding complex-values sequence S(k), k=0, 1, . . . , (N/log2(M))−1 as S(k)=S(k−1)exp(jφk) k=1, 2, . . . , (N/log2(M))−1, where S(0)=exp(jπ/M) and the relationship between the bit stream b(n) and the phase change φk is given in the tables 2100, 2200, 2300 of FIGS. 21-23 for π/2-DBPSK (M=2), π/4-DQPSK (M=4), or π/8-D8PSK (M=8), respectively.
As previously mentioned, a compliant device is able to support transmission and reception in one of the following frequency bands: 402-405 MHz, 420-450 MHz, 863-870 MHz, 902-928 MHz, 950-956 MHz, 2360-2400 MHz and 2400-2483.5 MHz. FIG. 24 shows a table 2400 with center frequency and channel number relationship information in accordance with embodiments of the disclosure. The mapping functions g1(nc) and g2(nc) used in the 420-450 MHz and 863-870 MHz frequency bands are respectively defined
as ⁢ ⁢ g 1 ⁡ ( n c ) = { n c 0 ≤ n c ≤ 1 n c + 6.875 2 ≤ n c ≤ 4 n c + 13.4 n c = 5 n c + 35.025 6 ≤ n c ≤ 7 n c + 40.925 8 ≤ n c ≤ 9 n c + 47.25 10 ≤ n c ≤ 11 , ⁢ and ⁢ ⁢ g 2 ⁡ ( n c ) = { n c 0 ≤ n c ≤ 7 n c + 0.5 n c = 8 n c + 1 9 ≤ n c ≤ 12 n c + 1.5 n c = 13 .
FIG. 27 shows a table 2700 with inter-frame spacing parameter information in accordance with embodiments of the disclosure. As shown, the parameter SIFS has a value equal to pSIFS and the parameter MIFS has a value equal to pMIFS. In at least some embodiments, pSIFS is approximately 50 μs and pMIFS is approximately 20 μs as shown in table 2600 of FIG. 26. Other parameters are also related to the pSIFS and pMIFS values. For example, the Receive-to-Transmit (RX-to-TX) turnaround time is equal to or less than pSIFS. The RX-to-TX turnaround time is defined as the time elapsed from when the last sample of the last received symbol is present on the air interface, to the time when first sample of the first transmitted symbol of the PLOP preamble for the next frame is present on the air interface. Further, the Transmit-to-Receive (TX-to-RX) turnaround time is equal to or less than pSIFS. The TX-to-RX turnaround time is defined as the time elapsed from when the last sample of the last transmitted symbol is present on the air interface until the time when the receiver is ready to begin the reception of first sample for the next PHY frame. Further, for burst mode transmissions, the inter-frame spacing between uninterrupted successive transmissions by a device shall be fixed to pMIFS. The inter-frame spacing is defined as the time elapsed from when the last sample of the last transmitted symbol is present on the air interface, to the time when the first sample of the first transmitted symbol of the PLOP preamble for the following packet is present on the air interface. Further, the center frequency switch time is defined as the interval from when the PHY transmits or receives the last valid symbol on one center frequency until it is ready to transmit or receive the next symbol on a different center frequency. In at least some embodiments, the center frequency switch time does not exceed the pChannelSwitchTime value in table 2600 (i.e., 100 μs).
The modulation accuracy of the transmitter is determined via an error-vector magnitude (EVM) measurement, which is calculated over N baud-spaced received complex values (Îk, {circumflex over (Q)}k). A decision is made for each received complex value. The ideal position of the chosen symbol is represented by the vector (Ik,{circumflex over (Q)}k). The error vector (δIk,δQk) is defined as the distance from the ideal position to the actual position of the received complex values, i.e., (Îk,{circumflex over (Q)}k)=(Ik,Qk)+(δIk,δQk).
EVM = 1 N ⁢ ∑ k = 1 N ⁢ ⁢ ( δ ⁢ ⁢ I k 2 + δ ⁢ ⁢ Q k 2 ) S 2 × 100 ⁢ % ,
a transceiver with a physical (PHY) layer, wherein the PHY layer is configured for body area network (BAN) operations in a limited multipath environment based on a constant symbol rate for BAN packet transmissions and based on M-ary PSK, differential M-ary PSK or rotated differential M-ary PSK modulation,
wherein the PHY layer is configured to transmit and receive data in a frequency band selected from the group consisting of: 402-405 MHz, 420-450 MHz, 863-870 MHz, 902-928 MHz, 950-956 MHz, 2360-2400 MHz, and 2400-2483.5 MHz, and wherein modulation accuracy is determined as an error-vector magnitude (EVM) measurement
computed over N baud-spaced received complex values (Îk, {circumflex over (Q)}k), where error vector (δIk, δQk) is the distance from an ideal position to an actual position of the received complex values and S is the magnitude of the vector to an ideal constellation point,
wherein the EVM measurement is measured on baseband I and Q samples after a received signal is passed through a reference receiver that performs the following operations: matched square-root-raised-cosine filter (SRRC) filtering, carrier-frequency offset estimation and symbol timing recovery while making the EVM measurements.
2. The communication device of claim 1, if the PHY layer uses π/2-DBPSK modulation, the EVM is equal to or less than 20%.
3. The communication device of claim 1, if the PHY layer uses π/4-DQPSK modulation, the EVM is equal to or less than 12.5%.
4. The communication device of claim 1, if the PHY layer uses π/8-D8PSK modulation, the EVM is equal to or less than 7.0%.
US12/760,516 2009-04-14 2010-04-14 PHY layer parameters for body area network (BAN) devices Active 2031-08-11 US8488655B2 (en)
US13/917,435 US9036614B2 (en) 2009-04-14 2013-06-13 PHY layer parameters for body area network (BAN) devices
US14/709,549 US9510138B2 (en) 2009-04-14 2015-05-12 PHY layer parameter for body area network (BAN) devices
US15/332,138 US10057745B2 (en) 2009-04-14 2016-10-24 PHY layer parameters for body area network (BAN) devices
US16/039,412 US20190037379A1 (en) 2009-04-14 2018-07-19 Phy layer parameters for body area network (ban) devices
US17288909P Substitution 2009-04-27 2009-04-27
US13/917,435 Continuation US9036614B2 (en) 2009-04-14 2013-06-13 PHY layer parameters for body area network (BAN) devices
US20100260162A1 US20100260162A1 (en) 2010-10-14
US8488655B2 true US8488655B2 (en) 2013-07-16
US20120314737A1 (en) * 2011-04-08 2012-12-13 Emerick Vann Systems and methods for transceiver communication
CN103493558B (en) 2011-04-11 2017-10-24 Lg电子株式会社 The method of channel switching in a medical body area network
EP2705682B1 (en) 2011-05-02 2018-02-28 Koninklijke Philips N.V. Mban channel use regulation scheme and adaptive channelization for ieee 802.15.4j standardization
JP5618944B2 (en) * 2011-08-19 2014-11-05 株式会社東芝 Wireless receiver
EP2749103B1 (en) 2011-12-05 2019-02-20 Koninklijke Philips N.V. Electronic key convey solution for in-hospital medical body area network (mban) systems
Agilent Technologies, CMMB Design Library, ADS 2009 Update 1, Oct. 2009 update 1, pp. 12-15. *
US9872130B2 (en) 2018-01-16
US8254303B2 (en) 2012-08-28 Efficient control signaling over shared communication channels with wide dynamic range
Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:BATRA, ANUJ;SCHMIDL, TIMOTHY M.;HOSUR, SRINATH;AND OTHERS;SIGNING DATES FROM 20100415 TO 20100419;REEL/FRAME:024268/0612