Source: https://patents.google.com/patent/US8626093B2/en
Timestamp: 2019-02-18 08:49:00
Document Index: 743550785

Matched Legal Cases: ['Application No. 60', 'Application No. 60', 'Application No. 60', 'Application No. 60', 'Application No. 60', 'Application No. 60', 'Application No. 60', 'Application No. 60', 'Application No. 60', 'Application No. 60', 'Application No. 60']

US8626093B2 - RF power transmission, modulation, and amplification embodiments - Google Patents
US8626093B2
US8626093B2 US13/561,723 US201213561723A US8626093B2 US 8626093 B2 US8626093 B2 US 8626093B2 US 201213561723 A US201213561723 A US 201213561723A US 8626093 B2 US8626093 B2 US 8626093B2
US13/561,723
US20130033313A1 (en
2006-12-12 Priority to US11/636,970 priority patent/US8233858B2/en
2012-07-30 Assigned to PARKERVISION, INC. reassignment PARKERVISION, INC. ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: SORRELLS, DAVID F., RAWLINS, GREGORY S., RAWLINS, MICHAEL W.
2012-07-30 Priority to US13/561,723 priority patent/US8626093B2/en
2012-07-30 Application filed by ParkerVision Inc filed Critical ParkerVision Inc
2013-02-07 Publication of US20130033313A1 publication Critical patent/US20130033313A1/en
2014-01-07 Publication of US8626093B2 publication Critical patent/US8626093B2/en
The present application is a continuation of pending U.S. patent application Ser. No. 11/636,970 filed on Dec. 12, 2006 which is a continuation of U.S. patent application Ser. No. 11/508,989 filed Aug. 24, 2006, which claims the benefit of U.S. Provisional Patent Application No. 60/794,121 filed on Apr. 24, 2006, U.S. Provisional Patent Application No. 60/797,653 filed on May 5, 2006, and U.S. Provisional Patent Application No. 60/798,705 filed on May 9, 2006, and is also a continuation-in-part of U.S. patent application Ser. No. 11/256,172, filed Oct. 24, 2005, which claims the benefit of U.S. Provisional Patent Application No. 60/620,972 filed on Oct. 22, 2004, U.S. Provisional Patent Application No. 60/671,542 filed on Apr. 15, 2005, U.S. Provisional Patent Application No. 60/671,536 filed on Apr. 15, 2005, U.S. Provisional Patent Application No. 60/673,397 filed on Apr. 21, 2005, U.S. Provisional Patent Application No. 60/706,003 filed on Aug. 8, 2005, U.S. Provisional Patent Application No. 60/709,092 filed on Aug. 18, 2005, U.S. Provisional Patent Application No. 60/717,244 filed on Sep. 16, 2005, and U.S. Provisional Patent Application No. 60/721,114 filed on Sep. 28, 2005, all of which are incorporated herein by reference in their entireties.
FIG. 1 illustrates a phasor representation of a signal
The term signal envelope, when used herein, refers to an amplitude boundary within which a signal is contained as it fluctuates in the time domain. Quadrature-modulated signals can be described by r(t)=i(t)·cos(ωc·t)+q(t)·sin(ωc·t) where i(t) and q(t) represent in-phase and quadrature signals with the signal envelope e(t), being equal to e(t)=√{square root over (i(t)2+q(t)2)}{square root over (i(t)2+q(t)2)} and the phase angle associated with r(t) is related to arctan(q(t)/i(t).
r(t)=I(t)·cos(ωt)+Q(t)·sin(ωt)=R(t)·cos(φ(t))·cos(ωt))+R(t)·sin(φ(t))·sin(ωt) (1)
wherein I1 and I2 represent the normalized magnitudes of phasors {right arrow over (I1)} and {right arrow over (I1)}, respectively, and wherein the domains of I1 and I2 are restricted appropriately according to the domain over which equation (2) and (3) are valid. It is noted that equations (2) and (3) are one representation for relating the relative phase shifts to the normalized magnitudes. Other, solutions, equivalent representations, and/or simplified representations of equations (2) and (3) may also be employed. Look up tables relating relative phase shifts to normalized magnitudes may also be used.
The concept describe above can be similarly applied to the imaginary phasor or the quadrature component part of a signal r(t) as illustrated in FIG. 4. Accordingly, at any time instant t, imaginary phasor part {right arrow over (Q)} of signal r(t) can be obtained by summing upper and lower phasor components {right arrow over (QU)} and {right arrow over (QL)} of substantially equal and constant magnitude. In this example, {right arrow over (QU)} and {right arrow over (QL)} are symmetrically shifted in phase relative to {right arrow over (Q)} by an angle set according to the magnitude of {right arrow over (Q)} at time t. The relationship of {right arrow over (QU)} and {right arrow over (QL)} to the desired phasor {right arrow over (QU)} are related as defined in equations 2 and 3 by substituting Q1 and Q2 for I1 and I2 respectively.
{right arrow over (Q U)}+{right arrow over (Q L)}={right arrow over (Q)}; (4)
Q U =Q L=constant;
r ⁡ ( t ) = I U ⁡ ( t ) + I L ⁡ ( t ) + Q U ⁡ ( t ) + Q L ⁡ ( t ) ; ⁢ ⁢ I U ⁡ ( t ) = sgn ⁡ ( I → ) × I UX × cos ⁡ ( ω ⁢ ⁢ t ) + I UY × sin ⁡ ( ω ⁢ ⁢ t ) ; ⁢ ⁢ I L ⁡ ( t ) = sgn ⁡ ( I → ) × I UX × cos ⁡ ( ω ⁢ ⁢ t ) - I UY × sin ⁡ ( ω ⁢ ⁢ t ) ; ⁢ ⁢ Q U ⁡ ( t ) = - Q UX × cos ⁡ ( ω ⁢ ⁢ t ) + sgn ⁡ ( Q → ) × Q UY × sin ⁡ ( ω ⁢ ⁢ t ) ; ⁢ ⁢ Q L ⁡ ( t ) = Q UY × cos ⁡ ( ω ⁢ ⁢ t ) - sgn ⁡ ( Q → ) × Q UY × sin ⁡ ( ω ⁢ ⁢ t ) . ⁢ I UX = I U × cos ⁡ ( ϕ I 2 ) = I L × cos ⁢ ( ϕ I 2 ) , ⁢ where ⁢ ⁢ I UY = I U × sin ⁡ ( ϕ I 2 ) = I L × sin ⁡ ( ϕ I 2 ) , ⁢ Q UX = Q U × sin ⁡ ( ϕ Q 2 ) = Q L × sin ⁡ ( ϕ Q 2 ) , and ⁢ ⁢ Q UY = Q U × cos ⁡ ( ϕ Q 2 ) = Q L × sin ⁢ ( ϕ Q 2 ) . ( 6 )
The embodiment illustrates a multiple-input single-output (MISO) implementation of the amplifier of FIG. 7A. In the embodiment of FIG. 7B, constant envelope signals 761, 763, 765 and 767, output from vector modulators 760, 762, 764, and 766, are input into MISO PAs 784 and 786. MISO PAs 784 and 786 are two-input single-output power amplifiers. In an embodiment, MISO PAs 784 and 786 include elements 770, 772, 774, 776, 794-797 as shown in the embodiment of FIG. 7A or functional equivalence thereof. In another embodiment, MISO PAs 784 and 786 may include other elements, such as optional pre-drivers and optional process detection circuitry.
Further, MISO PAs 784 and 786 are not limited to being two-input PAs as shown in FIG. 7B. In other embodiments as will be described further below with reference to FIGS. 51A-H, PAs 784 and 786 can have any number of inputs and outputs.
FIG. 8C is a block diagram that illustrates another exemplary embodiment 800C of vector power amplifier 700. Optional components are illustrated with dashed lines, although other embodiments may have more or less optional components. The embodiment of FIG. 8C illustrates a multiple-input single-output (MISO) implementation of the amplifier of FIG. 8A. In the embodiment of FIG. 8C, constant envelope signals 761, 763, 765 and 767, output from vector modulators 760, 762, 764, and 766, are input into MISO PAs 860 and 862. MISO PAs 860 and 862 are two-input single-output power amplifiers. In an embodiment, MISO PAs 860 and 862 include elements 770, 772, 774, 776, 794-797 as shown in the embodiment of FIG. 7A or functional equivalence thereof. In another embodiment, MISO PAs 860 and 862 may include other elements, such as optional pre-drivers and optional process detection circuitry.
In another embodiment, MISO PAs 860 and 862 may include other elements, such as pre-drivers, not shown in the embodiment of FIG. 7A. Further, MISO PAs 860 and 862 are not limited to being two-input PAs as shown in FIG. 8C. In other embodiments as will be described further below with reference to FIGS. 51A-H, PAs 860 and 862 can have any number of inputs and outputs.
{right arrow over (R′)}={right arrow over (U′)}+{right arrow over (L′)} (8)
|{right arrow over (U)}|=|{right arrow over (L)}|=A=constant
Equations (11) imply that a representation of {right arrow over (Rin)} can be obtained by summing phasors {right arrow over (U′)} and {right arrow over (L′)}, described above, shifted by θ degrees. Further, an amplified output version, {right arrow over (Rout)}, of {right arrow over (Rin)} can be obtained by separately amplifying substantially equally each of the θ degrees shifted versions of phasors {right arrow over (U′)} and {right arrow over (L′)}, and summing them. FIG. 9B illustrates this concept. In FIG. 9B, phasors {right arrow over (U)} and {right arrow over (U)} represent θ degrees shifted and amplified versions of phasors {right arrow over (U′)} and {right arrow over (L′)}. Note that, since {right arrow over (U′)} and {right arrow over (L′)} are constant magnitude phasors, {right arrow over (U)} and {right arrow over (L)} are also constant magnitude phasors. Phasors {right arrow over (U)} and {right arrow over (L)} sum, as shown FIG. 9B, to phasor {right arrow over (Rout)} which is a power amplified version of input signal {right arrow over (Rin)}.
where rout(t) corresponds to the time domain signal represented by phasor {right arrow over (Rout)}, U(t) and L(t) correspond to the time domain signals represents by phasors {right arrow over (U)} and {right arrow over (U)}, and K is the power amplification factor.
Output signals 1264 and 1266 represent substantially constant envelope signals. Further, phase shifts of output signals 1264 and 1266 relative to Rclk signal 1250 are determined by the angle relationships associated with the ratios α/C and β/C, respectively. In an embodiment, α=−β and therefore output signals 1264 and 1266 are symmetrically phased relative to Rclk signal 1250. With reference to FIG. 9B, for example, output signals 1264 and 1266 correspond, respectively, to the {right arrow over (U′)} and {right arrow over (L′)} constant magnitude phasors.
where R represents the normalized magnitude of phasor {right arrow over (U′)}.
(A being a constant). α and β denote the quadrature amplitude components of phasors {right arrow over (U′)} and {right arrow over (L′)}, respectively
FIG. 14 illustrates phasor {right arrow over (R)} and its two constant magnitude constituent phasors {right arrow over (U)} and {right arrow over (L)}. {right arrow over (R)} is shifted by θ degrees relative to {right arrow over (R′)} FIG. 9A. Accordingly, it can be verified that:
{right arrow over (U)}={right arrow over (U′)}×e jθ
(C+jα)(cos θ+j sin θ)=(C cos θ−α sin θ)+j(C sin θ+α cos θ). (16)
{right arrow over (L)}=(C+jβ)(cos θ+j sin θ)=(C cos θ−sin θ)+j(C sin θ+cos θ). (17)