Source: https://patents.google.com/patent/KR101197810B1/en
Timestamp: 2019-12-16 02:30:37
Document Index: 354516795

Matched Legal Cases: ['Application No. 60', 'Application No. 60', 'Application No. 10', 'Application No. 10', 'Application No. 10', 'Application No. 10', 'Application No. 10', 'Application No. 10', 'Application No. 10', 'Application No. 10', 'Application No. 10', 'Application No. 10', 'art 1000']

KR101197810B1 - Method and system for antenna interference cancellation - Google Patents
KR101197810B1
KR101197810B1 KR20067012072A KR20067012072A KR101197810B1 KR 101197810 B1 KR101197810 B1 KR 101197810B1 KR 20067012072 A KR20067012072 A KR 20067012072A KR 20067012072 A KR20067012072 A KR 20067012072A KR 101197810 B1 KR101197810 B1 KR 101197810B1
KR20067012072A
KR20060123350A (en
에드워드 게바라
앤드류 조 김
조이 라스카
엠마노일 엠. 텐트제리스
？란 인코포레이티드
2003-11-17 Priority to US60/520,592 priority
2004-11-17 Application filed by ？란 인코포레이티드 filed Critical ？란 인코포레이티드
2006-12-01 Publication of KR20060123350A publication Critical patent/KR20060123350A/en
2012-11-05 Publication of KR101197810B1 publication Critical patent/KR101197810B1/en
A wireless communication system is disclosed that includes two or more antennas that interfere with each other through free space coupling, surface wave crosstalk, and dielectric leakage. The interference effect can provide an interference signal to one of the antennas. The cancellation device can suppress antenna interference by generating an estimate of the interference signal and reducing the estimate from the interference signal. The cancellation device may generate an estimate based on a sampling signal at the antenna causing interference or the antenna receiving the interference. The cancellation device may include a model of a crosstalk effect. The transmission test signal of the communication system defines or refines the model.
Interference signal, antenna, phase shift, free space, frequency response
The present invention enjoys the benefit of priority over a patent application filed on November 17, 2003, entitled “Improved Operation of Nearly Positioned Antennas,” and entitled US Provisional Patent Application No. 60 / 520,592. The content of U.S. Provisional Patent Application No. 60 / 520,592 is incorporated by reference of the present invention.
The present invention is filed on March 28, 2002, entitled " Compound Stage Signal Decoding System and Method, " and the US Beam City Patent Application No. 10 / 108,598 and " Noise Filtering for Fastest Complex Stage Signal Decoding " And Equalization of the invention filed on July 15, 2003, with the US Beam City Patent Application No. 10 / 620,477, and the invention "System and method for crosstalk cancellation" on August 5, 2004. And a non-national beam city patent application number 10 / 911,915. The contents of US Patent Application No. 10 / 108.598 and US Patent Application No. 10 / 620,477 and US Patent Application No. 10 / 911,915 are incorporated herein by reference.
TECHNICAL FIELD The present invention relates to the field of wireless communications, and more particularly, to improve signal operation of a communication system having two or more adjacent antennas by compensating for crosstalk and coupling interference that may impair antenna operation.
There is a need for a wireless communication system having a large capacity or bandwidth in response to an increasing demand for data as the consumption of communication services increases. Phenomena known as crosstalk and interference often occur in such communication systems and damage high-speed signal transmissions, thereby limiting wireless communication bandwidth and degrading the quality to undesirable steps.
Crosstalk and related interference is a phenomenon in which signals from one communication channel or antenna are mixed with another channel or antenna or a superimposed structure, housing, material, active device or conductor. Such interference can occur due to various effects including current leakage, surface wave propagation, line interference, and electromagnetic coupling.
Crosstalk has emerged as an obstacle that markedly prevents an increase in the throughput of a wireless communication system. Crosstalk is often manifested as noise. More specifically, crosstalk increases signal uncertainty, thereby degrading signal quality, reducing communication reliability and increasing the probability of data errors occurring. In other words, crosstalk is typically more problematic as the data rate increases. Crosstalk not only reduces signal integrity, but also slows data communications by often increasing the amount of crosstalk in bandwidth.
Typical wireless communication systems, circuit boards, connectors, and transmission lines handle input and output communication signals entering or leaving through a communication antenna. In high speed communications, conductor paths, connectors and transmission line pickups and electromagnetic energy radiation on the circuit boards of the system can interfere with the operation of the receive and transmit antenna systems. The energy radiated from one antenna or combined conductor channel may be undesirably combined or received with another antenna or a channel associated with it. Such undesirable transmission of signal energy, known as "crosstalk" or "interference," can compromise signal or data integrity. Typical crosstalk that occurs bidirectionally on a single antenna or channel radiates energy to one or more other antennas or channels and receives energy from one or more other antennas or channels.
Compressed radios are particularly susceptible to antenna-to-antenna crosstalk. Antennas in close proximity to such systems can enhance the effect of crosstalk and severely degrade the signal. Such interference can affect composite antenna radio applications, where each antenna is delivered in the same crosstalk or in separate crosstalks. In addition, interference between antennas can impair operation, whether each antenna operates at the same frequency or at a particular frequency. In applications involving "global positioning sensors" (GPS), wireless fidelity ("WiFi"), "bluetooth" or other wireless standards, each of the two interfering antennas of a wireless device may operate at different frequencies and may Supply one of the services. The same crosstalk is a omnidirectional antenna system with two or more antennas that transmit leakage coupling and other applications may distort the radiation pattern of each antenna. The radiation pattern may be more affected than other omnidirectional antennas whether the antenna is operating in band or out of band.
Omnidirectional antennas typically involve the use of two or more antennas to accommodate complex instances of the same signal. The consequences of signal excess make the system robust against many factors, such as antenna type, antenna orientation and beam obstruction, which can degrade signal reliability. However, interference to one of the composite antennas can typically negate the utility of the technology in combination with an omnidirectional antenna when the antennas are close to each other. In addition, it is advantageous to avoid unnecessary dependence on the keep alive antenna for increased gain in power accounting.
In a composite antenna system, it is generally desirable to maintain the proper level of the isolation antenna, whether the antenna transmits clear or unclear signals. A minimum shield of 15 dB is generally suitable for most applications. Using conventional techniques such as shielding makes it difficult to produce miniaturization devices, such as for pockets, where the antennas are physically close together. Without proper shielding, reducing the space between antennas can negatively affect gain, directivity, throughput, beam shape, reachability, efficiency, and receiver sensitivity. The amount of antenna-to-antenna coupling that increases with the proximity of the antenna separation and the distance of 17-33% wavelength [lambda] is often a compromise between antenna shielding and miniaturization. In an effort to increase minimization, conventional cancellation device systems have provided a limiting step of shielding between interfering antennas. One type of conventional cancellation device system samples interference signals from a transmitting antenna and generates an cancellation signal specified in magnitude and phase for canceling the leakage signal affected by adjacent antennas. These prior arts generally have high frequency currents and place limitations on leakage signals that are not called other forms of interference such as surface wave crosstalk and free space coupling. Surface wave crosstalk can occur when electromagnetic waves propagate along the surface of a circuit board, mounting, or other structure in which two or more antennas are adjacent. The electromagnetic field patterns of adjacent antennas can be influenced each other through free space coupling, undesirably distorted or published in airborne media.
Conventional cancellation device systems strive to maintain the shielding of the signal, so that the transmit antenna works with the input signal close to the receive antenna to reduce the mixing of the output signal. However, such conventional cancellation device systems are not generally referred to as all of the phenomena that can cause antenna-to-antenna interference or crosstalk. For example, as a physical entity, the receive antenna can distort the radiation pattern of the system even when the receive antenna is in passive or idle mode. Such distortion may cause the receiving antenna to radiate energy undesirably and may wind up the pattern length near the transmitting antenna. As a physical presence, the receiving antenna may distort the adaptability of another receiving antenna. In general, conventional erasing device techniques overlooked such secondary radiation effects that could occur in free space. In other words, such conventional cancellation device systems typically cancel leakage-type crosstalk that occurs within the device, but are not often applied to crosstalk between two antenna field patterns in free space.
What is needed to correct representative defects of the art lies in the ability to cancel crosstalk between two or more antennas placed in physical proximity to each other. The ability to cancel crosstalk between two antennas via free-space coupling or via surface wave propagation is also required. Such capabilities promote broad lobe and increase signal performance in wireless communication applications involving small devices.
The present invention provides compensation for signal interference such as crosstalk between two antennas or more than two antennas. Compensation for crosstalk in wireless communication systems can improve signal quality and enhance bandwidth or information delivery capabilities.
Transmission of communication signals through one antenna may combine or impose unwanted signals such as interference or crosstalk to other antennas. An antenna that carries a communication signal may be referred to as a transmit antenna, while an antenna that transmits an imposed crosstalk may be referred to as a receive antenna. Such a combination in a wireless communication system may degrade or hinder the performance of one or both antennas, such as bandwidth limitations or signal degradation.
In one aspect of the invention, the cancellation device typically applies the cancellation signal to a receiving antenna that receives the interference signal imposed by the transmitting antenna. The cancel signal suppresses, cancels, reduces, minimizes, cancels, or otherwise compensates for interfering signals, shielding between antennas or improving performance. The cancellation device may generate, configure, and produce an cancellation signal based on a signal sampled or connected from a transmission antenna or a reception antenna.
In another aspect of the invention, the cancellation device may generate the cancellation signal by sampling the interference signal from the receive antenna or processing the sample signal. The processing of the sample signal may consist of a device for adjusting the phase and magnitude of the sample signal having a signal processing device for supplying an cancellation signal combined with the interference signal. The device for adjusting the phase and magnitude of the sample signal may be included as a device that slightly delays the vibration or period of the signal, such as a variable phase adjuster, or slightly hinders the propagation speed of the sample signal. The sample signal adjusting device may include, for example, a device for expanding, proportioning, and enhancing a sample signal such as a variable gain amplifier. The cancellation device can apply the cancellation signal to the receiving antenna to cancel the transmitted interference signal. For example, the cancellation device may remove the cancellation signal from the interference signal through a combiner that introduces the cancellation signal into the supply line of the receiving antenna. The cancellation device may include a controller that dynamically controls, tunes, and modifies the phase and magnitude to smooth or update the effects of interference cancellation. The cancellation device may measure the cancellation effect by observing the degree of residual or uncanceled interference energy present in the receiving antenna after cancellation. The controller can use the observed energy or power as a feedback signal to smooth the adjustment of phase or magnitude. While canceling the interference, the receiving antenna may be idle or inactive, for example, away from the transmitting communication signal while the transmitting antenna is in an active state of the transmitting communication signal.
In still another aspect of the present invention, the cancellation apparatus may generate an cancellation signal by sampling a communication signal of a transmitting antenna or processing a sample signal. The sample signal processing apparatus may be included as a device for supplying a sample signal into the model of the interference effect. The model may generate or produce a cancellation signal as an estimate or counter of the interference signal. The cancellation device can cancel a significant portion of the interference, for example, by applying a cancellation signal to the reception antenna by removing the cancellation signal from the signals transmitted by the reception antenna. The erasing device may comprise a controller that dynamically adjusts or adapts the model for purifying the cancellation signal, thus increasing or canceling the erasing effect in the operating environment. The controller can observe the residual energy in the receive antenna and adjust the model to minimize the observed energy. The cancellation device can inject test signals into the antenna system and observe the interference produced by these test signals. The controller can analyze the interference stimulated by the test signal and can refine the model based on the analysis.
The review of the canceled or corrected interference provided in this summary is for illustrative purposes only. Various aspects of the invention may be more clearly understood or appreciated by reviewing the following detailed description of the invention or by reference to the drawings and claims.
Many aspects of the invention will be better understood with reference to the following drawings. The components in the figures are intended to clearly illustrate the principles of the exemplary embodiments of the invention, so proportionality or emphasis is not essential. Thus, reference numerals in the drawings refer to corresponding parts throughout the several angles.
1 is an exemplary layout diagram of two crosstalk canceling devices applying two antennas according to an embodiment of the present invention.
2 is a functional block diagram of an exemplary crosstalk cancellation apparatus in a wireless communication system according to an embodiment of the present invention.
3A and 3B are exemplary simulation results for a system composed of two antennas before and after crosstalk cancellation according to an embodiment of the present invention.
4A, 4B, and 4C illustrate exemplary stimulated antenna electromagnetic fields for a single antenna before and after crosstalk cancellation in a system consisting essentially of two shielded antennas in accordance with an embodiment of the present invention.
5A is an illustration of an exemplary system consisting of two access antennas in accordance with an embodiment of the present invention.
5B is a representative signal dotted diagram for a connected antenna system prior to interference cancellation in accordance with an embodiment of the present invention.
6A and 6B are representative signal dotted diagrams of a paired antenna before and after interference cancellation according to an embodiment of the present invention.
7 is an exemplary layout diagram of a system consisting of two crosstalk cancellation devices coupled in parallel between two antennas in accordance with an embodiment of the present invention.
8 is a functional block diagram of an exemplary system having a crosstalk cancellation device coupled to two antennas in accordance with an embodiment of the present invention.
9 is an exemplary diagram of multiple curves of interference in which two antennas are combined as a function of frequency for a variable phase alignment value in accordance with an embodiment of the present invention.
10 is a flowchart of an exemplary process for cancellation of crosstalk or interference in one antenna in accordance with an embodiment of the present invention.
The present invention provides interference compensation or crosstalk cancellation consisting of two or three antennas in a wireless communication system. Exemplary methods or systems for crosstalk cancellation enhance the signal performance of two antennas located near each other, such as elements in a portable or handheld small wireless communication device.
This invention may be embodied in many different forms and should therefore not be construed as limited to the foregoing embodiments. Rather, the examples will make the disclosure more complete and complete and will fully transmit the scope of the invention to those skilled in the art. In addition, all examples given herein are not intended to be limiting, and therefore are provided by embodiments of the invention among other examples.
Referring to FIG. 1, this diagram shows a crosstalk cancellation device coupled to supply lines 160, 165 of each antenna 110, 115 and two antennas 110, 115 close to another cancellation device 175a, 175b. Represents a communication system 100 having a.
The system 100 typically operates while one of the two antennas 110, 115 is at rest and the other antennas 110, 115 actively transmit signals. The mode of each antenna 110, 115 may vary during normal operation of the system. In other words, one of the antennas 110, 115 is inactive, inactive, idle, inactive, i.e., inactive mode, while the other antennas 110, 115 are in transmit mode. In the illustrated operating state, one antenna 115 is in active mode while the other antenna 110 is in idle mode. One antenna 115 transmits a communication signal and the other antenna imposes interference on the other antenna 110. Thus, in the illustrated state, one antenna 115 is referred to as transmit antenna 115. And, the other antenna 110 is referred to as the receiving antenna 110 because it receives interference from the transmitting antenna 115.
In forming crosstalk interferences 180, 185, 190, the transmission or coupling of signal energy from the transmit antenna 115 to the dormant receive antenna 110 may impair the performance of the transmit antenna 115. Among other adverse effects, the transmission of unwanted radiant energy may distort the active electromagnetic field pattern of the transmitting antenna 115.
The cancellation device 175a can cancel the crosstalk interference 180, 185, 190 on the idle reception antenna 110 imposed by the active transmission antenna 115 on the reception antenna 110. While the transmit antenna 115 is active, the cancellation device 175a remains in a state of not providing inactive or active cancellation.
In the reverse operating state (not shown), one antenna 115 is at rest and the other antenna 110 is active. In this state, the erasing device 175b erases by applying one antenna 110 to the other antenna 115. And the other erasing device 175a is inactive.
If both antennas 110 and 115 are active, the two cancellation devices 175a and 175b are typically turned off or in inactive mode. The two antennas 110 and 115 may transmit a common payload simultaneously to extend the overall gain of the system 100. Thus, the cancellation device configuration of the system 100 provides for interference cancellation in a diversity antenna system while one or more antennas transmit during at least one other time the system is idle, inactive or non-transmitting. Small communication devices such as cell phones, GPS, radios, walkie-talkies, portable calculators, laptop computers, palmtop computing systems may include the system 100. Such a communication device may further comprise a duplexer or associated power amplifier (“PA”) to which the antenna supply lines 165 and 160 are coupled, a transmitting electronic device and a receiving electronic device (not shown).
The cancellation devices 175a and 175b can reduce or cancel various forms of interference or crosstalk 180, 185 and 190 that damage the antennas 110 and 115 of the system or impair signal performance. Exemplary forms of such crosstalk or interference may include surface waves 190, free space coupling 180, and dielectric leakage 185. Such crosstalk can occur in one or both directions while the system is operating. Accordingly, each of the antennas 110 and 115 may be an interference generator and an interference receiver. In other words, each of the two antennas 110 and 115 can be both a cross-talker and a cross-talk victim. For example, the transmit antenna 115 may impose an interference signal on the dormant receive antenna 110. The dormant antenna 110 may radiate back the interference imposed on the transmitting antenna 115 in a manner that disrupts the electromagnetic field pattern of the transmitting antenna 115 with a standing wave, for example.
Surface wave 190, which is a typical electromagnetic signal, may propagate along the surface of the dielectric material from transmit antenna 115 to dormant receive antenna 110. For example, each of the antennas may be mounted on a board of a circuit board passing through or through a hole in a circuit board through which the supply lines 160 and 165 pass. The surface wave 190 may propagate along the surface of a circuit board that typically includes a dielectric material such as resin or ceramic. This unwanted transmission of energy can negatively affect the signal performance of the system 100. The cancellation device 175a can cancel such surface wave crosstalk or interference.
Free space coupling 180 is the coupling of RF electromagnetic signals in a free space medium in the open atmosphere between the antennas 110 and 115. The dormant antenna may draw RF energy from the transmit antenna. The presence of the dormant antenna 110 in the vicinity of the transmit antenna 115 may undesirably distort the electromagnetic field pattern of the transmit antenna 115. Such crosstalk or interference can negatively affect the performance of the transmit antenna if left unchecked. The cancellation device 175a can enhance antenna shielding by interference cancellation due to free space coupling.
In addition, crosstalk or interference 185 due to dielectric leakage may deteriorate signal integrity of the antennas 110 and 115. Dielectric leakage 185 may occur when allowing incomplete insulators, such as a flawed dielectric material, to flow through an RF electromagnetic signal. A portion of the flowing RF signal may pass through the dormant antenna and interfere with the intended signal of the antenna. The erasing device 175a may cancel crosstalk or interference 185 due to dielectric leakage.
The system's erasing devices 175a, 175b address interference or interference caused by one or more phenomena such as surface wave coupling 190, free space coupling 180, dielectric leakage 185 (an exhaustive list). Can be erased and erased. Each antenna 110, 115 has cancellation devices 175a, 175b associated with respective supply lines 160, 165, respectively. As discussed above, each cancellation device 175a, 175b supplies active cancellation during the time that the one antenna 110, 115 connected thereto is idle and the other antenna 110, 115 is active. By canceling the crosstalk interference effects 180, 185, 190 these cancellers 175a, 175b improve the shielding level between the antennas 110, 115. The combination of each signal of the antennas 110, 115 provides an improved integrity of the transmitted communication signal and an improved antenna radiation pattern. Such improvements enhance efficiency, directivity, beam shape, throughput, and reach.
Each erasing device 175a, 175b releases or samples a substantial portion of the interfering signal on its respective supply lines 160, 165 as a reference signal. Based on this reference signal, each erasing device 175a, 175b generates an erasing signal applied to its respective supply lines 160, 165, respectively. Thus, when the antenna 110 is at rest and the other antenna 115 is actively transmitting a communication signal (as shown), the cancellation device 175a samples the interference on the supply line 160 and a reference signal. Using sampled signals. Based on the processing of the reference signal, the erasing device 175a generates an erasing signal and applies the erasing signal to the supply line 160.
The application of the cancellation signal to the supply line 160 by the cancellation device 175a cancels and reduces the interference signal that the transmission antenna 115 may impose on another dormant antenna 110. The erasing device 175a adjusts the magnitude, phase, and timing of generating an erasing signal for canceling the interference signal on the supply line 160. In other words, the cancellation device 175a samples the interference signal or waveform on the supply line 160 and produces an cancellation signal with appropriate magnitude, phase, and timing characteristics, which cancels the crosstalk interference on the antenna 110. Cancel and cancel out.
2, which is a functional block diagram of an exemplary crosstalk cancellation device 175a in a wireless communication system 100. The system 100, which may be like the system 100 depicted in FIG. 1, includes two cancellation devices 175a and 175b coupled to the supply line of each antenna. On the other hand, the two erasing devices 175a and 175b typically include the same functional elements. For clarity, FIG. 2 shows an exemplary functional block diagram of the erase device 175b rather than the other erase device 175a. Thus, the two erase fields 175a and 175b may be two copies of the standardized module.
As shown in FIG. 2 (and a similar system 700 is shown in FIG. 8 and will be discussed below), the distribution of system 100 and crosstalk canceller 175a into functional blocks, modules, and respective submodules is: Those skilled in the art will recognize that it is only conceptual and not necessarily mandatory to indicate clear boundaries of device functionality or substantive grouping. Rather, the drawings are based on functional block diagrams and are used to describe embodiments of the present invention as representative of the embodiments. Indeed, such modules may be combined, divided and redistributed within other modules without departing from the spirit and scope of the invention.
The cancellation device 175a includes a phase adjuster 220, a delay adjuster 225, a variable gain amplifier (“VGA”) 260, two dividers 210. 230, a subtraction node 290, and a power detector 240. And a controller 250. The distributor 210 samples the interference signal that excites the other inactive dormant antenna 110. The signal processing circuit 275 including the phase adjuster 220 and the VGA 260 is named by adjusting the phase and magnitude of the sample signal, respectively, for processing the sample signal. The plus node 290 cancels the interference by applying a phase shifted and scaled signal generated by the signal processing circuit 275 to the supply line 160 of the dormant antenna 110. The delay adjuster 225 times the cancel signal and the interference signal to coincide with the idle antenna 110. The distributor 230 samples the signal on the supply line 160 to cancel the crosstalk. The power detector 240 measures the power level of the remaining unwanted signal and provides the resulting measurement to the controller 250 as a feedback control signal. Based on these energy or power measurements, the controller 250 dynamically adjusts and tunes the VGA 260, the delay adjuster 225, and the phase adjuster 220 to refine the interference cancellation. The functional blocks of the erasing device 175a shown hereafter will be discussed in more detail individually.
The distributor 210, the other distributor 230, and the plus junction 290 may each include a coupler. As used herein, the term combiner refers to a signal that combines an electrical or electromagnetic signal from or in a signal channel. Exemplary couplers 210, 230, 290 of the system 100 include three ports. Two of the ports are connected to the transmission line 160, and the third port passes a signal that the combiner 210, 230, 290 extracts from the transmission line 160 or introduces into the transmission line 160. As will be discussed in more detail below, the combiner 210, 230, 290 of the cancellation device extracts a sample, feeds back a signal from the supply lines 160, 165 and introduces an erase signal into the supply lines 160, 165. .
The divider 210 adjacent to the dormant antenna 110 samples the interference signal coupled to the antenna 110 from the adjacent transmit antenna 115 via free space coupling 180 or other crosstalk effects. In other words, the divider 210 taps a large portion of the signal energy transmitted from the radiating antenna 115 to the inactive receiving antenna 110 as a result of the proximity of these two antennas 110, 115. The divider 210 thus captures a representative of the reference signal of interference. The erasing device 175a owns the captured reference signal through the signal processing circuit 275 in order to generate an erasing signal, and returns to the antenna supply line 160 to cancel the interference.
In an embodiment of the invention the distributor 210 is an inactive directional coupler. In an alternative to the present invention, the dispenser 210 may include an activity circuit. The divider 210 typically exhibits a relatively high input impedance at the tap off point. For example, the divider 210 may provide 50 ohms to match the impedance characteristics of other discrete elements of the erase device 175a. In other words, the elements of the erasing device 175a may be impedance matched at 50 ohms or other suitable impedance characteristic value.
The impedance characteristic of the divider 210 provides for operation of the antenna 110 in idle or active mode. At tap off, the divider 210 should have a high impedance to avoid the effect of supply through the line characteristic impedance. When the antenna 110 is in the active mode of the transmit signal (as opposed to the operating state shown), the cancellation device 175a is typically in an inactive or off mode that does not produce an erase signal. In order to provide antenna operation when the cancellation device 175a is in such an inactive mode, the distributor 210 introduces as little or as little loss as possible into the signal path of the antenna supply line 160. In other words, the divider 210 should avoid the cause of excessive loss through the signal path, which may result in poor performance of the antenna 110. Excessive loss in the signal path of the supply line 160 may damage the transmission / reception signal and cause a decrease in reception sensitivity.
To further support antenna 110 operation in both active and inactive modes, divider 210 and other divider 230, plus node 290 and the delay adjuster (as well as other elements in the signal path of the supply line). 225 is bidirectional.
In an embodiment of the present invention, the signal path of the supply line 160 includes loss compensation to compensate for any device in the signal path that introduced the loss. Increasing the gain of the PA or low noise amplifier (“LNA”) may provide loss compensation. A gain block cannot generally be introduced between the antenna 110 and the duplex because most gain blocks are unidirectional devices that are affected by the bidirectionality of the system.
In an embodiment, an erase device 175a is introduced between the PA and the duplexer. In this alignment, the LNA path will remain untouched and will not be subject to the loss strikes of the erase device 175a. However, the gain block need not be introduced next to the PA in the erasing device 175a.
In yet another embodiment, the erase device 175a has a bypass mode. When the erasing device 175a is turned off, a signal going through the supply line 160 bypasses the erasing device 175a through the bypass mode. Using a bypass configuration is typically the preferred approach for lost emission addresses when some bypass bypass is needed to improve the gain of the PA or the LNA.
Reference is now made to the operating modes shown. The phase adjuster 220 receives a sampled signal from the divider 210 and performs a phase match in the addition mode 290 between the phase of the interference signal propagating through the transmission / reception signal path of the supply line 160 and the cancellation signal. Adjust the phase to feed. In other words, the phase adjuster 220 supplies phase synchronization and alignment between the cancellation signal applied to the supply line 160 and the interference on the supply line 160.
In an embodiment, the phase adjuster 220 adjusts the phase of the cancellation signal such that the phase difference of the interference signal is 180 degrees from the interference signal at the application point where the cancellation signal may include the plus node 290. If the cancellation signal is in phase with the interference signal, then the plus node 290 subtracts the cancellation signal from the interference signal (as shown). On the other hand, if the cancellation signal and the interference signal are 180 degrees out of phase, the addition node 290 adds these signals in turn.
In an embodiment of the invention, the phase shifter 220 comprises a quadrature hybrid or four silicon hyper-abrupt junction diode supported by conventional resistors, inductors and capacitors. In one embodiment, the phase shifter 220 includes an active circuit.
The VGA 260 receives the phase shifted or matched cancellation signal from the phase adjuster 220 and propagates to the supply line 160 of the dormant antenna 110 at the node 290 in addition to the magnitude of the signal. Match the interference signal. In other words, the VGA 260 amplifies the cancellation signal to provide an amplitude and magnitude that matches the interference signal on the supply line 160.
The plus node 290 applying the cancellation signal to the supply line 160 may be an inactive directional coupler or an active circuit. As discussed above with respect to the divider 210, the plus node 290 should not introduce significant impedance mismatches into the transmit and receive paths of the antenna supply line 160.
The adjustable delay adjuster 225 matches the group of interference signals propagated through the path of the supply line 160 to the group delay of the cancellation signal propagated through the condensation of the signal processing circuit 275. In other words, the delay adjuster 225, which may be referred to as an adjustable delay, is the signal processor circuit 275 along the path of the supply line 160 associated with the signal delay occurring between the divider 210 and the plus node. Compensate for signal delays that occur between divider 210 and the plus node 290.
The divider 230 samples the canceled signal and supplies it to the power detector 240. In other words, the divider 230 provides a sample of the residual signal on the supply line 160 as a result of applying the cancellation signal at the node 290 to the interference signal. If the cancellation signal is effective, the residual signal has less power and energy than the cancellation signal is not effective. The power detector 240 monitors this canceled signal as a feedback signal that supplies as an indicator of the cancellation effect and supplies the monitored power to the controller 250. The controller 250 includes the GVA 260, the phase adjuster 220, according to a feedback signal that provides an cancellation signal for properly canceling and eliminating crosstalk interference between the supply line 160 and the antenna 110. The delay adjuster 225 is adopted and controlled.
More specifically, the controller 250 acquires values of phase, delay, and gain that provide the minimum energy on the supply line 160. Phase, delay, and gain are adjusted to reduce the amount of interference by experience or to a predetermined or minimal level. Mismatch of phase or delay mismatch and magnitude can adversely affect the improvement of the overall transmitted signal quality on the transmit antenna 115. In other words, the controller 250 identifies the GVA 260 to identify the operating point for each of these devices such that the signal power on the supply line 160 is minimized or transmitted RF energy while the antenna 110 is idle. ), The delay adjuster 225 and the phase adjuster 220 are operated. The minimum signal power of the dormant antenna 110 and its supply line 160 minimizes the fluctuation of this antenna due to the transmit antenna 110 which is the intended training of the communication signal.
The controller 250 includes logic elements such as wired or fixed and programmable logic. The controller 250 includes a microprocessor, microcomputer or other computing processor, such as an application specipic integrited circuit (ASIC). In addition such logic elements, the controller includes, for example, circuitry, connection electronics, power supplies, storage devices and the like.
US Unconditional Patent Application No. 10 / 108,598 is entitled “Methods and Systems for Decoding Murphy Level Signals” and filed on March 22, 2002, various exemplary systems and methods for evaluation signals have been published. US Unconditional Patent Application No. 10 / 620,477 is an invention entitled "Adopted Sleep Filtering and Equalization for Optimal Fast Multilevel Signal Decoding" and filed on July 15, 2003, the phase adjuster 220, the VGA 260, the delay adjuster. Various exemplary systems and methods for the control device parameters of 225 have been disclosed. U.S. Patent Application No. 10 / 108,598 and US Patent Application No. 10 / 620,477 is fully incorporated by reference. One or more of the phase adjuster 220, the VGA 260 and the delay adjuster 225 are described in US Patent Application No. 10 / 108,598 and US Patent Application No. Can be controlled and / or adjusted, respectively, using the systems and / or methods disclosed in 10 / 620,477. The parameters of these devices 220, 260, 225 may, for example, be described as potential values after the publication of this patent application. The parameters removed through that area can be determined by processing the parameters of each device.
3A and 3B, these diagrams illustrate the simulation of the antenna system 300 before and after crosstalk interference in accordance with an embodiment of the present invention. More clearly, these figures show a reduction through the electromagnetic coupling between two antennas 110 and 115 where the reception and transmission of the interfering signal is achieved by canceling the interfering transmitted signal occurring above the dormant or non-transmitting antenna 110. . The integrity of the white pattern on the black background shows the stimulated surface current distribution for the pair of small foldable dipole antennas 110, 115 spaced 0.1 lambda (0.1 lambda) apart. In an embodiment, the antenna shown in FIGS. 1 and 2 may be the small foldable dipole antennas 110, 115 of FIGS. 3A and 3B, and may be referred to as mentioned in FIGS. 3A, 3B, 4A and 4B. .
3A illustrates surface current distribution in a system 300a operating in an uncompensated state. Unlimited surface currents show crosstalk coupling between antennas 110 and 115 that lack antenna shielding. The transmit antenna 115 excites the dormant antenna 110 due to the spread and dispersion of the surface current between the two antennas 110, 115.
FIG. 3B shows a simulation of the results of the crosstalk cancellation application through the erasing device 175a drawn in FIGS. 1 and 2 and discussed above. In other words, the cancellation device 175a improves the performance of the transmission antenna 115 by applying crosstalk cancellation to the idle antenna 110. As shown by the minimum or near-near current distribution above the idle antenna 115, the cancellation device 175a reduces the unintentional coupling between antennas 110. 115 to a value close to zero. In other words, the limitation of the surface current of the active antenna 115 is related to the shielding improvement of this antenna 115.
Referring to Figures 4A, 4B and 4C, these figures show the antenna electromagnetic field patterns before and after crosstalk cancellation 300a and 300b respectively for a single antenna 115 which is an original shielded two antenna system according to an embodiment of the present invention. Show simulations of (425, 450, 475). Each figure provides a three-dimensional illustration of the respective electromagnetic field patterns 425, 450, and 475. As will be appreciated by those skilled in the art, the figure shows patterns 425, 450, 475 of electromagnetic fields and conveys information in an intuitive manner. Accordingly, this figure 425, 450, 475 complements the current density examples 300a, 300b of FIGS. 3A, 3B discussed above and illustrates the beneficial results provided by the crosstalk canceller 175a.
Figure 425 of FIG. 4A provides simulation data from a single foldable dipole antenna that is not easily disturbed from other antennas 110. FIG. Clearly, the illustrated electromagnetic field pattern 425 is the result of simulating the operation of the transmit antenna 115 shown in FIGS. 3A and 3B in the absence of an adjacent dormant antenna 110. The electromagnetic field pattern 425 resulting from the operation of this fully shielded antenna 115 provides a standard for evaluating the results of applying the crosstalk canceller 175a to the interference pair of the antenna 300a. In other words, the simulated single antenna 115 is inherently shielded from interference. The direction of antenna radiation pattern 425 is 4.9 dBi.
As one of ordinary skill in the art will understand, directionality is a measure of the focus of an antenna beam pattern in a given direction. Theoretical loss-minimum antenna material, called isotopes, has a direct gain variance of 0.0 dBi in all three dimensions. In other words, isotope antennas are theoretical clerks that radiate power equally in all directions to create a perfect sphere pattern.
In order to achieve greater direct gain in the direction of interest, most antennas focus and concentrate the electromagnetic field pattern of the antenna in a particular direction, such as the receiver direction, to maximize energy transfer. For example, most connecting antennas have a beam pattern directed in one direction to shoot a significant portion of the energy perpendicular to the application plane.
The unit of "dBi" refers to decibels ("dB") representing the ratio between the power of a given antenna and the corresponding isotope antenna power. Thus, "dB" represents 10 times the logarithm of the base of the ratio 10. Larger dBi values correspond to greater gain and higher focus range. For example, an antenna having a gain of 10 dB in a particular direction provides 10 times more gain than that of an isotope antenna in a particular direction.
4B shows a simulation pattern for two antenna systems 300a. Here the second antenna 110 is at rest and is 0.1 lambda away from the transmit antenna 115, as depicted in FIG. 3A and discussed above. Transmit antenna 115 shows a radiation pattern with a directivity of 3.9 dBi. Thus, the presence of the second interfering antenna 115 gives the maximum gain of the pattern from 4.9 dBi to 3.9 dBi.
FIG. 4C shows a simulation pattern for two antenna systems 300a, which is the result of applying crosstalk cancellation to the idle antenna 110 through the crosstalk cancellation device 175a discussed above with reference to FIG. 3B. When the crosstalk cancellation device 175a is active, the antenna 115 produces a radiation pattern with a directionality of 4.7 dBi.
On the other hand, in the presence of the unmodified dormant antenna 110, the antenna pattern 450 of the active antenna 115 is compared to the single-antenna 425 electromagnetic pattern 427, so that the modified electromagnetic pattern is the single-antenna. It shows reduced, focusing and distortion similar to the electromagnetic pattern. In other words, the interference cancellation device 175a reorients and reforms the transmitted beam pattern of the active antenna 115 to achieve shielding and to meet a particular result. The cancellation device 175a restores the gain direction to a value within 0.2 dBi of the direction of the original shielded single antenna 115. Thus, the simulated cancellation removes most of the interference of the active antenna 115 imposed by the adjacent idle antenna 110.
Beam recovery by the cancellation device 175a can improve the 3 to 4 dB gain for the antenna 115 in the design direction of the emission maximum. The organizational effect of these improvements can result in, for example, transmission distance, an improvement of four to five, a 40% reduction in the required antenna power, and a bit error rate ("BER") improvement of ten.
5A, there is shown a system 500 that includes two patch antennas 510, 515 in accordance with a preferred embodiment of the present invention. The antennas 510 and 515 are made of a substrate made of FR4, which is a synthetic material generally used for circuit boards. A version of the antenna system 500 is fabricated with spaces of [lambda] / 10, [lambda] / 8, [lambda] / 8, [lambda] / 4, and [lambda] / 2 between the single antennas 510,515. The physical distances between the patch antennas 510, 515 for each of the five manufactured systems 500 are 1/10, 1/8, 1/6, and 1 / 2λ of the transmitted communication signal wavelength. On the other hand, one of the antennas 510, 515 may be dormant or active, and the antenna 515 will act as a transmit antenna while the antenna 510 operates as a dormant antenna.
5B, there is shown a graph of representative signal diagrams 565, 570, 575, 580, 585 for a patch antenna system 500 prior to interference cancellation in accordance with a preferred embodiment of the present invention. One of the tests in each laboratory of each of the five antenna systems 500 is a patch antenna 515 in which a frequency varying stimulus signal is transmitted. At the same time, the experimental instruments are monitored with power coupled to different patch antennas 510 according to frequency.
Thus, the pilot 550 represents a frequency between 1 GHz and 4 GHz between two antennas 510 and 515 in relative coupling.
All of the signal diagrams 565, 570, 575, 580, 585 have a floor at about 2.4 GHz, indicating the strongest crosstalk coupling at this frequency. The trend of the populations of curves 565, 570, 575, 580, 585 shows the effect of crosstalk interference that increases with a decrease in the independent space between the antennas 510, 515. Coupling for differently located antenna pairs 500 varies from 15 to 28 dB at 2.4 GHz. Each coupling degree 585, 580, 575, 570, 565 of the antenna pairs has antenna-to-antenna separation of λ / 2, λ / 4, λ / 6, λ / 8, and λ / 10, and antenna 510 515) to enhance separation between them. The test data shows the strongest coupling for the patch antennas 510, 515 spaced λ / 10 apart.
As a preferred embodiment of the present invention, the patch antenna pair 500 operates in a WiFi application, conforms to standards provided by the Institute of Electrical and Electronics Engineers (IEEE) under IEEE 802.11, or specifically provided by the present invention. Or the coding protocol in paragraph g. The IEEE 802.11b standard is an improvement over IEEE 802.11 that provides data rates of 5.5 and 11 megabits per second. The IEEE 802.11g standard represents a protocol for wireless communication with data of 54 megabits per second at 2,4 GHz.
6A and 6B show signal diagrams 600 and 650 of a pair 500 of patch antennas 510 and 515 before and after interference cancellation in accordance with an embodiment of the present invention. The signal diagrams 600 and 650 show laboratory test data for the patch antenna pair 500 shown in FIG. 5 and described above.
Pilot 600 of FIG. 6A shows two transmit power spectra 610, 620 for patch antennas spaced λ / 10 apart. The trajectory 620 represents test data obtained prior to applying interference cancellation. In contrast, the trajectory 610 represents test data obtained while the interference cancellation according to an embodiment of the present invention is applied. Specifically, the test conditions included in the application of interference cancellation are associated with the cancellation provided by the cancellation device 175a referenced and described with reference to FIGS.
The transmit patch antenna 515 is provided with a fixed phase input power. The patch antenna 510 is idle during the test and interferes with the operation of the active antenna 515. The trajectory 620 represents the transmitted power of the antenna without interference cancellation. In contrast, trajectory 610 represents the transmitted power of the antenna during interference cancellation. The difference between the two test traces 610 and 620 is approximately 1.08 dB. Under laboratory test conditions, the interference cancellation device 175a is provided with an antenna gain improvement of about 1.08 dB. Thus, crosstalk cancellation provides an antenna system 500 with improved transmit power.
The pilot of FIG. 6B shows the measured data of the electromagnetic signal on the idle antenna 510 before and after crosstalk cancellation. The trajectory 660 is generated by measuring the signal on the dormant antenna 510 without interference cancellation while the active antenna 515 transmits the RF communication signal by electromagnetic field radiation. Conversely, trajectory 670 shows the signal captured from dormant antenna 510 while active antenna 515 outputs a signal and cancellation device 175a suppresses interference. The difference between these two trajectories 660 and 670 indicates that the cancellation device 175a provides a 32 dB improvement in antenna shielding. An example of application of crosstalk cancellation reduced to undesirable power transmits from the transmit antenna 515 to the dormant antenna 510.
Referring to FIG. 7, there is shown a system 700 comprising two crosstalk cancellation devices 750a, 750b coupled to a parallel arrangement between two antennas 110, 115 in accordance with one embodiment of the present invention. . The system 700 of FIG. 7 and the system 100 shown in FIG. 1 may include the same antennas 110, 115 and antenna supply lines 160, 165, and may be capable of crosstalk interference 180, 185, 190. It can accept communication damage from the same form. However, the operating mode of these systems 100 and 700 and the erasing devices 170 and 750 can be clarified.
Referring to FIG. 7, the cancellation devices 750a and 750b may appear as interference in a system having antennas transmitting different frequencies as well as interference in the omnidirectional antenna. Antennas 110 and 115 of the system 700 may transmit signals at distinct frequencies, respectively. In addition, the system 700 may send signals continuously from both antennas 110 and 115, or may receive signals from the antennas 110 and 115 continuously during crosstalk cancellation. The crosstalk cancellation devices 750a and 750b may provide inner and outer lobe interference cancellation. Crosstalk cancellation results can improve receptor sensitivity and radiation pattern.
The cancellation devices 750a and 750b are connected in parallel arrangement between the antennas 110 and 115. The erasing device 750a applies crosstalk cancellation to the antenna 115 through the supply line 165 while the erasing device 750b provides erasing to the antenna 110 through the supply line 160. The result of the cancellation device arrangement provides bidirectionality for each antenna 110, 115. In this arrangement, both cancellation devices 750a and 750b can cancel interference at the same time, and both antennas 110 and 115 actively transmit a signal. Thus, each of the antennas 110, 115 can be a receiving antenna and a transmitting antenna at the same time.
The erasing device 750a connects the reference signal to the supply line 160 of the antenna 110 and processes the reference signal to generate an erase signal applied to the supply line 165 of the antenna 115. Applying the cancel signal to the receive antenna 115 cancels or suppresses the interference imposed on the receive antenna 115 by the transmit antenna 110.
The cancellation device 750b operates in a consistent manner but on the other hand connects the reference signal from the antenna 115 and applies the cancellation signal generated to the antenna 110. In this direction of operation, the antenna 115 acts as a transmit antenna 115 and the antenna 110 acts as a receive antenna 110.
Referring to Fig. 8, there is shown a block diagram of a system 700 having crosstalk cancellation devices 750a and 750b connected between two antennas 110 and 115 in accordance with a preferred embodiment of the present invention. The system 700 of FIG. 8 may be the same as the system 700 shown in FIG.
The components and arrangement of the crosstalk canceller 750b are crossed relative to the crosstalk canceller 750a to provide unidirectional crosstalk cancellation of each of the cancellers 750a and 750b. According to one embodiment of the invention, the single integrated unit comprises erasing devices 750a, 750b.
According to one embodiment, the erase devices 750a and 750b have the same arrangement and are essentially the same. Thus, each of the erasing devices 750a, 750b can be a copy of the erasing device module, and has pins for the distributors 840, 850 and the general node 860, 870. As applied to antennas 110 and 115 operating at the same frequency, a pin from each cancellation device module may be connected to appropriate antenna supply lines 160 and 165 to provide the system structure shown in FIG. . However, if each of the antennas 110, 115 operates at a clear frequency, each of the cancellation devices 750a, 750b has a unique emulation filter 810 corresponding to the operating frequency of the antennas 110, 115. do.
According to one preferred embodiment of the present invention, the system 700 includes transmitter and receiver electronics (not shown) coupled to each antenna supply line 160, 165. Each of the antennas 110 and 115 may be a transceiver antenna for transmitting and receiving wireless signals. Dual communicators (not shown) can separate the direction of entering and exiting the appropriate circuit path. The dual communicator may command an input signal from the antenna 110 to a receiver and an output signal from the transmitter to the antenna 110. The PA (not shown) may enlarge the output signal radiating from each of the antennas 110 and 115. The PA is not disposed between the dual communicator and the antennas 110 and 115 associated therewith, and the signal path between the dual communicator and the antennas 110 and 115 is bidirectional, while the PA directs the signal in a single direction. Deal with. In addition, the PA is on the receiving side of the duplexer and is opposite the antenna. In other words, components such as a PA are not bidirectional and typically are not disposed between the duplexer and the respective antennas 110, 115.
The operation block and operation of the erasing device 750a will be outlined. The distributor 840 samples the signal received at the supply line 160 of the reception antenna 110. The model 825 processes the sample to generate an estimate of the interfering signal imposed on the receiving antenna 115 by the signal received at the antenna 110.
Phase adjuster 220 and delay adjuster 225 and VGA 260 of model 825 are sampled to match the interference at antenna 115 for application at the summation node 870. Adjust the phase, timing, and amplitude of the signal respectively. The emulation filter 810 can rotate after modeling the channel coupling to compensate for drift at the center frequency of the channel.
The controller 820 adjusts the phase adjuster 220, the channel emulation filter 810, the delay adjuster 225, and the VGA 260 based on the feedback provided to the power detector 240. The controller 820 further controls a voltage controlled oscillator (VCO) 830. In response to a command from the controller, the VCO 830 generates a pilot signal that injects the combiner 806 into the supply line 160 of the antenna 110. Via divider 850 and power detector 240, the controller observes antenna-antenna crosstalk in response to pilot signal stimulation. The controller 820 minimizes the received pilot signal; These pilot signals are combined via air or other interference mechanisms and processed by the signal processing circuit 825. Model 825 cancels the pilot signal, which is out of band relative to the operating frequency 115 of the receiving antenna. Pilot signals are not needed for omnidirectional antennas.
Based on the observed response, the controller 820 dynamically refines the model 825 by adjusting the phase adjuster 220, the emulation filter 810, the delay adjuster 225, and the VGA 260. The controller 820 includes logic elements such as logic by wiring, fixed logic, programmable logic, or the like. Controller 820 typically includes a microcontroller, a microprocessor, a microcomputer, or some other computing processor such as an ASIC or the like. Along with such logic elements, the controller includes, for example, support circuits, interface electronics, power supplies, memory, and the like.
The functional block of the eraser 750a is now described. Divider 840 obtains a sample of the signal transmitted on supply line 160, which transmits a communication signal to antenna 110 in the form of RF energy. The sample signal may include a communication signal to spread from the antenna 110. The distributor 840 may be a passive directional coupler or an active circuit, as described with reference to the distributor 210 of the system 100 shown in FIG. 2. In addition, the distributor 840 is basically the same component as the distributor 210. Dividers 840 and 850 and global nodes 860 and 870 each include a combiner and may include three signal ports.
As described with reference to distributor 210 of FIG. 2, distributor 840 should have an impedance match that matches the impedance characteristics of the other components coupled to supply line 160 and should not exhibit excessive loss characteristics. . In addition, divider 840 must have a high impedance at the connection point to avoid drawing excessive power from supply line 160.
If loss compensation is taken in the signal path that takes a non-bidirectional amplifier stage or other device type, then the device must be placed in the portion of the signal path with a non-bidirectional signal flow responsive to the device's directivity. Thus, if necessary, loss compensation should be applied to the transmitter / receiver side of the duplexer that the system 700 includes, not between the duplexer and its associated antenna.
In one embodiment of the invention, the divider 840 is disposed between the duplexer and the antenna 110. In this form, the canceller 750a can model any coupled interference nonlinearity induced in the system 700 by the duplexer and / or the associated PA.
Optionally, divider 840 may be disposed between the duplexer and the PA, which PA is on the opposite side of the duplexer relative to antenna 110 as described below. Dispenser 840 may be disposed in front of the PA. However, this form is undesirable in most applications because the nonlinearity induced in the system by the PA is not modeled by the canceller 750a.
The preferred location of the general node 870 is between the antenna 115 and the duplexer. If the overall node 870 is placed behind the duplexer, i.e. between the duplexer and the LNA, the canceller 750a is another form that improves receiver sensitivity. It does not contribute sufficiently to the improvement of the aggressive antenna signal integrity (ie beam shape, gain, directionality). Placing the generic node 870 behind the LNA does not provide an improvement in the attacked antenna signal integrity because the LNA is non-bidirectional. An improvement is the receiver sensitivity of the receiving antenna 115.
Divider 840 provides a signal sample to phase adjuster 220. As described with reference to Fig. 2, the phase adjuster 220 adjusts the phase of the erase signal to match the phase of the interference signal on the supply line 165 at the point where the erase signal is applied. As also described above, phase transfer 220 may provide 180 ° phase transfer if overall node 870 is reduced.
Phase adjuster 220 outputs a signal to emulation filter 810, referred to as a band pass (BP) channel emulation filter. The emulation filter 810 may rotate after modeling the channel coupling to compensate for drift at the center frequency of the channel.
As described above, as shown in FIG. 5B in the form of reference numeral 550, the coupling effect between the two antennas 110, 115 may exhibit a limited frequency response. Aging associated with antenna oxidation, for example, changes the coupling and center frequency of closely spaced antennas. Rapid frequency changes above and below 2.4 GHz contribute to the noise floor or dynamic range of the measurement system. Frequency deviations due to changes associated with the environment or aging cause changes in the strength and frequency of the interfering signals. By modeling the frequency response or channel of the coupling effect, the emulation filter 810 provides an emulated signal similar to the interference on the supply line 165 despite the change in the excitation signal on the source antenna 110. That is, the emulation filter 810 models the transmission function of the combined channel in the frequency domain to provide an cancellation signal having a frequency dependent characteristic that matches the actual interference on the antenna 115.
In one proposed embodiment, the emulation filter 810 includes a concentrator and a varactor diode. The varactor diode promotes a change in the center frequency of the emulation filter. In another embodiment of the present invention, the emulation bandpass filter 810 is a fine impulse filter (FIR), such as a tapped delay line filter or the like. The tap and tap spacings of these FIRs are extracted from closely spaced antenna coupling channel characteristics. In order to achieve a high level of antenna coupling cancellation for improved signal integrity of the system 700, the emulation filter 810 must match the coupling channel characteristics in the band of interest.
Co-owned US patent application Ser. No. 10 / 911.915, filed Aug. 5, 2004, entitled “Methods and Systems for Crosstalk Cancellation,” describes an exemplary, tapped delay line filter for modeling a crosstalk transmission function. System is disclosed. In one embodiment, the tapped delay line filter includes a plurality of delay elements coupled to a plurality of variable gain amplifiers. The US patent application Ser. No. 10 / 911.915 also discloses a viable example system and method for applying a crosstalk model using a controller that observes a channel signal. The contents of this US patent application Ser. No. 10 / 911.915 is incorporated herein by reference.
One or more of phase adjuster 220, VGA 260, delay adjuster 225, and emulation filter 810 are described in US patent applications 10 / 620.477 and 10 / 108.598, as described with reference to FIG. Controls and / or adjustments may be made using the methods and / or systems disclosed, respectively. The variables of such devices 220, 260, 225, 810 can be determined by treating each variable as a variable that is postmarked through a range of potential values, for example, following the contents of the patent specification.
The output of the emulation filter 810 is supplied to the input of the delay adjuster 225. The delay adjuster 225 matches the group delay of interference on the antenna 115 with the group delay of the emulated cancellation signal applied to the supply line 165 at the aggregate node 870.
The VGA 260 accepts an output of a delay adjuster 225; The amplitude of the emulated signal is adjusted to match the amplitude of the interfering signal at the general node 870. Unlike modeling an emulation filter of the frequency response of a crosstalk or interfering channel, the VGA 260 carries the level of the emulated signal to provide amplitude matching with the interfering signal at the supply line 165. By modeling the frequency response of the crosstalk effect, the emulation filter 810 produces an emulated signal, which has a waveform similar to that of the interfering signal at the supply line 165. On the other hand, the VGA 260 applies a gain to the emulated signal, imposing it on an amplitude or intensity that is almost similar to crosstalk interference.
The overall node 870, which may be a directional coupler or an active circuit, applies an emulated signal to the supply line 165 to cancel or cancel the interference. As described with respect to overall node 290 with reference to FIG. 2, the overall node 870 must have an impedance match that matches the impedance characteristics of the other components and impose excessive losses on supply line 165. Should not. The general node 870 is basically the same as the general node 290 of the system 100 described with reference to FIG.
The splitter 850, coupled with the supply line 165 of the antenna 115, samples the canceled signal and then sends it to a power detector 240 that observes the power or energy of the canceled signal associated with the canceled pilot signal. Supply. That is, divider 850 and power detector 240 measure the level of any residual or previously canceled interference remaining on antenna 115. The controller 820 uses this observed signal as feedback to adjust the phase adjuster 220, the emulation filter 810, the delay adjuster 225, and the VGA 260.
Under the control of the controller, the VCO 830 generates a test signal or a pilot signal, in which the general node 860 is inserted into the signal path of the supply line 160 of the antenna 110. The canceller 750a observes the response of the system 700 to this pilot signal in order to apply a cancellation signal to effectively cancel the interference. In particular, canceller 750a observes residual interference associated with the pilot signal.
The controller 830 controls, purifies the operation of the interference controller 750 using an appropriate approach to recognize the magnitude of the interference signal, the phase, the delay value in order to minimize the energy of the combined interference , Or optimize. In other words, the controller 820 may adjust the phase adjuster 220, the channel emulation filter 810, the delay adjuster 225, and the VGA 260 in a suitable manner to reduce or minimize the interference energy on the antenna 115. Dynamically adjust As discussed above, divider 850 and power detector 240 observe the level of interference energy.
Exemplary embodiments of system 700 may provide interference cancellation in three operational states. In one embodiment, the system 700 is operated for an omnidirectional antenna such that antenna 115 is at rest and antenna 110 is actively transmitting.
In these various applications, the cancellation device 750a can characterize the combined channel by canceling the crosstalk imposed on the receive antenna 115 without a pilot signal. Thus, this first embodiment may correspond to the mode of operation of the system shown in FIGS. 1 and 2 and discussed above.
In a second embodiment, the system 700 operates in conjunction with antenna 115 and antenna 110 operating at separate frequencies. In this scenario, the connection is made on antenna 115 via a communication signal combining channel transmitted on antenna 110. The cancellation device 750a injects two pilot signals to the antenna 110, which are connected on the antenna 115. One of these pilot signals has a frequency above the operating frequency of the antenna 115, while the other pilot signal has a frequency below the operating frequency of the antenna 115. The cancellation device uses this pilot signal to handle the interference.
In a third embodiment, the cancellation device 750 cancels crosstalk that occurs at antenna 110 and antenna 115 operating at essentially the same frequency. A third exemplary embodiment will be discussed in detail. Those skilled in the art will appreciate the applicability of the discussion of the second embodiment described in the immediately preceding paragraph.
With antenna 110 and antenna 115 operating at essentially the same frequency, two test or pilot signals inserted on antenna 110 may characterize the combined channel. The cancellation signal provided by the cancellation device 750a is continuously updated through two pilot signals, one having a frequency higher than the communication band of the system 700 and one having a frequency lower than that band. For a system communicating at 2.4 GHz, for example, one pilot signal may have a frequency of 2.45 GHz, while the other pilot signal may have a frequency of 2.35 GHz. Pilot signals located spectrally outside the communication band avoid interference between the pilot signal and the communication signal. VCO 830 alternately emits a high frequency pilot signal and then a low frequency pilot signal. Thus, at any particular time during the cancellation device operation, the coupling device 860 may be injected into one of the pilot signals, and the controller 820 may operate on the cancellation device based on the power measurement indicated by the power detector 240. Can be refined. In one embodiment, the erasing device 750a intermittently emits a pilot signal.
Turning now to FIG. 9, this figure shows a curve 905, 910, 915, 920, 930 of the interference coupling between two antennas 110, 115 as a function of frequency for various phase alignment values in accordance with an embodiment of the present invention. Shows a graph of a typical population.
The frequency range of the plot 900 extending from 2.4 to 2.5 GHz can be a band of typical frequencies at which the cancellation device 750a minimizes interference. In other words, the cancellation device 750a may cancel crosstalk interference that crosses a band of frequencies extending from 2.4 to 2.5 GHz.
Curve 970 represents the overall frequency response of the combined channel. Thus, antenna 110 is coupled to antenna 115, where the ratio of its energy to the frequency band is in the range between approximately 18.5 dB and approximately 13.5 dB.
Each of the curves 905, 910, 915, 920, 925, 930 represents the coupling ratio in dB for each phase alignment of 110 °, 90 °, 70 °, 10 °, 50 ° and 30 ° follow-up cancellation. Thus, each of these curves 905, 910, 915, 920, 925, 930 represents the level of resulting crosstalk that can be obtained by adjusting the phases of the cancellation signal as indicated by the cancellation device 175a. For example, if the phase adjuster 220 adjusts the phase of the cancellation signal relative to 110 °, the crosstalk coupling would be approximately -26.3 dB at 2.4 GHz, less than -40 dB at 2.44 GHz and less than -17 dB at 2.5 GHz. .
Graph 900 additionally shows a spectral representation of two superimposed pilot signals 970 and 950, one with a frequency close to 2.4 GHz and the other with a frequency close to 2.5 GHz. As discussed above, the cancellation device 750a can adjust the phase of the cancellation signal based on the relative coupling of these pilot signals between the antennas 110 and 115.
Retrofitting the cancellation device system using pilot one signal 940 results in an adjustment to the 90 ° phase optimal cancellation. In other words, if controller 820 operates the phase adjuster to minimize crosstalk coupling of pilot 1 signal 940, controller 820 will select 90 ° as the optimal phase. Fixing at 90 ° phase is optimal for pilot 1 signal 940 because curve 910 at 90 ° has the lowest coupling at the frequency of pilot signal 940.
However, for the pilot 2 signal 950, 90 ° adjustment in phase is not the optimal solution. At the frequency of pilot 2 signal 950, 90 ° phase adjustment in the cancellation signal provides approximately -19 dB of interference coupling. In other words, the 90 ° phase adjustment curve 910 has a value of approximately -19 dB at the frequency of the pilot 2 signal 950. At the frequency of the pilot 2 signal 950, a 30 ° phase adjustment does not provide an improved level of interference suppression according to the curve 930.
By adapting the cancellation signal based on two pilot signals 940,950 rather than just one, the controller can provide effective cancellation across the frequency band for a range between 2.4 GHz and 2.5 GHz. In one exemplary embodiment of the present invention, controller 820 averages the phase selection for pilot one signal 940 and the phase selection of pilot two signal 950. For example, the controller 820 calculates the 60 ° phase adjustment by averaging the 90 ° phase adjustment and the 30 ° adjustment.
Rather than a simple average, the controller 820 may also be a means of minimizing recurring errors in selecting a phase that crosses the frequency band of interest and provides effective cancellation. According to plot 900, a phase adjustment of approximately 70 ° provides optimal minimization of the combined signal. To identify this 70 ° operating point, the controller 820 may use a 60 ° phase adjustment as a starting point and then make increasing phase adjustment. If the feedback signal from the power detector 240 increases as a result of the gradual adjustment, the controller 820 is a means for increasing different phase adjustments. In this way, the controller 820 can start at 60 ° and adapt through iteration until it finds an optimal 70 ° phase adjustment. The controller 820 may continuously purge the cancellation signal in response to changing conditions such as environmental effects and frequency trends during normal operation.
Controller 820 may also use other incremental search or optimization methods known to those skilled in the art. In a typical embodiment of the present invention, a coordinate-descent approach as described in US patent application Ser. No. 10 / 620,477, discussed above, is based on measuring the system's response to test signal stimuli. Provides search and optimization to identify acceptable model variables.
Returning now to FIG. 10, this diagram illustrates a flow chart 1000 of a typical procedure for canceling crosstalk or interference on an antenna 115 in accordance with embodiments of the present invention under the name Cross Cancel. The steps of this procedure 1000 will be discussed as a typical reference for the system 700 of FIGS. 7 and 8 discussed above.
Certain steps in this procedure or other typical procedures described herein must naturally proceed with other steps for the present invention to function as described. However, the present invention is not limited to the order of the described steps unless such order or order changes the functionality of the present invention. In other words, it should be appreciated that some of the steps may be performed before or after another step or in parallel with other steps without departing from the scope and spirit of the present invention.
In step 1010, the first step of procedure 1000, the transmit antenna 110 transmits a communication signal. The transmitter (not shown) may supply a transmission signal to the supply line 160. The communication signal may for example be encrypted with voice information or data. The transmit antenna 110 emits a radiation pattern that a long range communication device (not shown) can receive.
In step 1015, the crosstalk effects 180, 185, 190 couple the energy of the communication signal transmitted from the transmit antenna 110 to the receive antenna 115. Interference signals that continue on receive antenna 115 include interference. As discussed above, the receive antenna 115 may also transmit communication signals while continuing to impose interference.
In step 1020, the interfering signal on the receive antenna 115 interferes with the operation or function of the transmit antenna 110. Such interference may distort the field pattern of the transmit antenna 115 or impair the original appearance and / or reception sensitivity of the communication signal.
In step 1025, the cancellation device 175a samples the communication signal on the transmit antenna 110. Specifically, the divider 840 taps off a portion of the signal on the supply line 160 of the transmit antenna 110.
In step 1030, the model 825 of the erasing device 750a processes a sample of the communication signal. Based on this procedure, this model 825 emits an estimate of the interfering signal that the receiving antenna 115 accepts. The cancellation signal contains this estimate. The model 875 processes the sample signal by means of a phase adjuster 220, an emulation filter 810, a delay adjuster 225, and a VGA 260. Phase adjuster 220 applies a phase delay to the sample signal. Emulation filter 810 filters the sample signal according to the filter parameters. Delay adjuster 225 delays the sample signal in time. VGA 260 is applied to augment the sample signal to provide amplification.
In step 1035, a summation node 870 is applied to the estimate or cancel signal at the receive antenna 115. In step 1040, the cancellation signals are mixed together and cancel the interfering signal on the receive antenna 115. This cancellation signal typically cancels out a significant amount of interfering signals, but not necessarily all of the interfering signals. In other words, residual levels of interference may remain un-cancelled.
At step 1045, the controller 820 emits a signal to the VCO 830. In response, VCO 830 generates test or pilot signals 940 and 950 of known frequency. Node 860 locates test signals 940 and 950 on supply line 160 of transmit antenna 110.
In step 1050, the test signals 940, 950 connect on the receive antenna 115 via one or more crosstalk effects 180, 185, 190. For example, some of the energy in the test signals 940, 950 can be transmitted to the receive antenna 115 via free space coupling.
In step 1055, the divider 850 branches some of the interference due to the test signals 940, 950 from the supply line 165 of the receive antenna 115. The power monitor 240 measures the power level of the extracted signal. The controller 820 analyzes the extracted signal. Specifically, the controller 820 measures the power level in the signal extracted at the frequencies of the test signals 940, 950. A more detailed discussion of the processing or analysis of the controller for the extracted signals or test signals 940, 950 is provided above with reference to FIGS. 7, 8, or 9.
In step 1060, the controller 820 adjusts modeling, phase shift, delay and gain in a dynamic manner corresponding to step 1055. The controller 820 adjusts each parameter, the operating point of the phase adjuster 220, the emulation filter 810, the delay adjuster 225 and the VGA 260. This adjustment improves the behavior of the model and allows to obtain repetitive improvements or to smooth the effects of the cancellation signal. More detailed discussion has been described above with respect to FIGS. 7, 8 and 9. As described later in step 1060, the process 1000 repeats steps 1010 to 1060.
The system according to the present invention may include compensation for crosstalk imposed on the communication signal by means of cancellation, correction or other signal, although such techniques are not limited to the embodiments of the invention described and described. It is further understood that various embodiments of the invention may be employed and practiced. The scope of the invention is not limited by the claims which follow.
Sampling a signal transmitted at the first antenna;
Processing the sampled signal according to the parameter to generate an estimate of the interference signal;
Applying an estimate of the interference signal to a second antenna to suppress the interference signal; And
Changing a parameter corresponding to monitoring the suppressed interfering signal,
The processing of the sampled signal may include filtering the sampled signal with a filter having a frequency response, applying phase shift to the sampled signal, delaying the sampled signal by time, and sampling according to the gain. Amplifying the signal, wherein varying the parameter comprises adjusting a frequency response, phase shift, time, and gain to suppress an interference signal imposed by the first antenna on the second antenna How to.
2. The method of claim 1, wherein the estimate of the interfering signal comprises an cancellation signal.
The method of claim 1, wherein the transmitted signal comprises a test signal and a communication signal.
The method of claim 1, further comprising: transmitting, at a first antenna, a first test signal having a first frequency, a second test signal having a second frequency, and a communication signal having a third frequency between the first frequency and the second frequency. Including,
And said sampling comprises sampling the transmitted first test signal and sampling the transmitted second test signal.
The method of claim 1, wherein the interfering signal is imposed by the first antenna on the second antenna via an interference effect,
Applying the pilot signal to a first antenna;
Transmitting at least a portion of the pilot signal from a first antenna to a second antenna via the interference effect; And
Specifying a model of interference effect based on monitoring a portion of the transmitted pilot signal, wherein the transmitted pilot signal comprises a communication signal and processing the sampled signal comprises: Applying a model to the communication signal.
2. The method of claim 1, wherein monitoring the suppressed interfering signal comprises connecting power from a supply line of a second antenna and measuring the connected power.
Transmitting a test signal at the first antenna;
Coupling a portion of the test signal through an interference effect from a first antenna to a second antenna;
Defining a model of the interference effect based on the processing of the test signal;
In response to transmitting the communication signal at the first antenna, coupling the interference over the second antenna via an interference effect;
Outputting an estimate of interference in response to processing a communication signal with the model; And
Applying the estimate to a second antenna to reduce the interference,
The model includes delaying the signal by filter, phase shift, time, and amplifying the signal according to gain,
Defining the model includes adjusting the frequency response, phase shift, time, and gain of the filter.
11. The method of claim 10, wherein processing the test signal comprises monitoring a portion of the test signal coupled to a second antenna.
11. The method of claim 10 wherein the interference effect comprises free space coupling.
11. The method of claim 10, wherein the interference effect comprises a dielectric leak.
11. The method of claim 10, wherein said interference effect comprises surface wave coupling.
11. The method of claim 10, wherein transmitting a test signal at a first antenna comprises supplying the test signal to a supply line of a first antenna via a first combiner, wherein applying the estimate to the second antenna Supplying said test signal to a supply line of a second antenna via a second coupler.
12. The method of claim 10, wherein applying the estimate to the second antenna comprises subtracting the estimate from a portion of the test signal coupled to the second antenna through the interference and crosstalk effects.
A first coupler having a port connected to a supply line of a dormant antenna for supplying a sample of the signal to a signal processing circuit; And
A second combiner including a port for supplying an erase signal to the supply line, wherein the signal processing circuit adjusts a sample of the signal in response to the changed frequency response of the filter, and applies a phase shift to the sampled signal, Delaying the sampled signal by time, amplifying the sampled signal according to gain, and generating the cancellation signal based on adjusting the frequency response, phase shift, time and gain. A system for canceling a signal coupled to an idle antenna by an active antenna.
And a third combiner for obtaining a feedback signal from said supply line and a controller for adjusting said gain and said phase shift based on said feedback signal.
19. The system of claim 18, wherein the first combiner comprises a distributor and the second combiner comprises a general node.
KR20067012072A 2003-11-17 2004-11-17 Method and system for antenna interference cancellation KR101197810B1 (en)
US60/520,592 2003-11-17
KR20060123350A KR20060123350A (en) 2006-12-01
KR101197810B1 true KR101197810B1 (en) 2012-11-05
KR20067012072A KR101197810B1 (en) 2003-11-17 2004-11-17 Method and system for antenna interference cancellation
JP3878811B2 (en) * 1999-03-03 2007-02-07 シーメンス アクチエンゲゼルシヤフトＳｉｅｍｅｎｓ Ａｋｔｉｅｎｇｅｓｅｌｌｓｃｈａｆｔ Frequency multiplexing transceiver and crosstalk cancellation method
AU2003239577A1 (en) 2002-06-21 2004-01-06 Qualcomm Incorporated Wireless local area network repeater
CA2502876A1 (en) 2002-10-15 2004-04-29 Widefi, Inc. Wireless local area network repeater with automatic gain control for extending network coverage
WO2011077247A2 (en) * 2009-12-21 2011-06-30 Dali Systems Co. Ltd Modulation agnostic digital hybrid mode power amplifier system and method
WO2013009664A1 (en) * 2011-07-08 2013-01-17 Google Inc. Control of sar in mobile transmit diversity systems employing beam forming by using coupling between diversity branches
JP6508052B2 (en) * 2013-09-26 2019-05-08 日本電気株式会社 Signal transmission apparatus, distortion compensation apparatus, and signal transmission method
CN106464284B (en) * 2014-06-26 2019-08-16 华为技术有限公司 A kind of device and method that interference is eliminated
WO2015196425A1 (en) 2014-06-26 2015-12-30 华为技术有限公司 Interference cancellation device and method
CN106464616B (en) 2014-06-26 2019-10-22 华为技术有限公司 A kind of device and method that interference is eliminated
WO2017069300A1 (en) * 2015-10-21 2017-04-27 엘지전자 주식회사 Method for controlling self-interference duplication signal for removing self-interference in environment supporting full-duplex radio (fdr) communication, and apparatus therefor
DE69326357D1 (en) 1992-05-05 1999-10-14 British Telecomm Optical switching device
JPH09502308A (en) 1994-06-20 1997-03-04 フィリップス エレクトロニクス ネムローゼ フェンノートシャップ Radiation-emitting semiconductor refractive index guiding type diode
CN100399626C (en) 2008-07-02 Adaptive cancellation of fixed interferers
KR20120128668A (en) 2012-11-27 Method and system of beamforming a broadband signal through a multiport network
CN102027636B (en) 2013-12-25 Calibrating radiofrequency paths of phased-array antenna
BR0315342B1 (en) 2018-01-09 &#34;antenna structure, radio device understanding antenna structure, and, radio apparatus&#34;
KR20090113917A (en) 2009-11-02 Physical layer repeater utilizing real time measurement metrics and adaptive antenna array to promote signal integrity and amplification
2012-01-10 AMND Amendment
2012-06-12 J201 Request for trial against refusal decision
2012-06-12 AMND Amendment