Source: http://www.freshpatents.com/-dt20121129ptan20120299775.php
Timestamp: 2015-05-25 05:32:06
Document Index: 568974179

Matched Legal Cases: ['Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No, 61', 'Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No, 61', 'Application No, 61']

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Active phased array architecture Title: Active phased array architecture.Abstract: In an exemplary embodiment, a phased array solid-state architecture has dual-polarized feeds and is manufactured, for example, on highly flexible silicon germanium (SiGe). The implementation of dual-polarized feeds facilitates the operation of phased arrays where the polarization can be statically or dynamically controlled on a subarray or element basis. In an exemplary embodiment, the sub-component control is configured to optimize a performance characteristic associated with polarization, such as phase or amplitude adjustment. An active phased array architecture may replace traditional distributed and GaAs implementations for the necessary functions required to operate electronically steerable phased array antennas. The architecture combines active versions of vector generators, power splitters, power combiners, and RF hybrids in a novel fashion to realize a fully or substantially monolithic solution for a wide range of antenna applications that can be realized with radiating elements having single-polarized or dual-polarized feeds, ...
Browse recent Viasat, Inc. patentsUSPTO Applicaton #: #20120299775 - Class: 342372 (USPTO) - 11/29/12 - Class 342 Inventors: David W. Corman, Kenneth V. Buer, Donald Lawson Runyon, Stefano Vacarro, Ferdinando Tiezzi, Daniel Llorens Del Rio, Donald E. Crockett The Patent Description & Claims data below is from USPTO Patent Application 20120299775, Active phased array architecture.
This application is a continuation of U.S. Ser. No. 12/759,130, filed on Apr. 13, 2011 and entitled “ACTIVE PHASED ARRAY ARCHITECTURE,” The '130 application is a non-provisional of U.S. Provisional Application No. 61/237,967, entitled “ACTIVE BUTLER AND BLASS MATRICES,” which was filed on Aug. 28, 2009. The '130 application is also a non-provisional of U.S. Provisional Application No. 61/259,375, entitled “ACTIVE HYBRIDS FOR ANTENNA SYSTEMS,” which was filed on Nov. 9, 2009. The '130 application is a non-provisional of U.S. Provisional Application No. 61/234,513, entitled “ACTIVE FEED FORWARD AMPLIFIER,” which was filed on Aug. 17, 2009. The '130 application is a non-provisional of U.S. Provisional Application No, 61/222,354, entitled “ACTIVE PHASED ARRAY ARCHITECTURE,” which was filed on Jul. 1, 2009. The '130 application is a non-provisional of U.S. Provisional Application No. 61/168,913, entitled “ACTIVE COMPONENT PHASED ARRAY ANTENNA,” which was filed on Apr. 13, 2009. The '130 application is also a non-provisional of U.S. Provisional Application No. 61/259,049, entitled “DYNAMIC REAL-TIME POLARIZATION FOR ANTENNAS,” which was filed on Nov. 6, 2009. The '130 application is a non-provisional of U.S. Provisional Application No. 61/234,521, entitled “MULTI -BAND MULTI-BEAM PHASED ARRAY ARCHITECTURE,” which was filed on Aug. 17, 2009. The '130 application is a non-provisional of U.S. Provisional Application No, 61/265,605, entitled “HALF-DUPLEX PHASED ARRAY ANTENNA SYSTEM,” which was filed on Dec. 1, 2009. The '130 application is a non-provisional of U.S. Provisional Application No, 61/222,363, entitled “BIDIRECTIONAL ANTENNA POLARIZER,” which was filed on Jul. 1, 2009. All of the contents of the previously identified applications are hereby incorporated by reference for any purpose in their entirety.
A phased array antenna uses multiple radiating elements to transmit, receive, or transmit and receive radio frequency (RE) signals, Phase shifters are used in a phased array antenna in order to steer the beam of the signals by controlling the respective phases of the RE signals communicated through the phase shifters. Phased array antennas are used in various capacities, including communications on the move (COTM) antennas, satellite communication (SATCOM) airborne terminals, SATCOM mobile communications, and SATCOM earth terminals. The application of mobile terminals typically requires the use of automatic tracking antennas that are able to steer the beam in azimuth, elevation, and polarization to follow the satellite's position while the terminal is in motion. Moreover, a phased array antenna is typically desired to be “low-profile”, small and lightweight, thereby fulfilling the stringent aerodynamic and mass constraints encountered in the typical mounting.
One well known type of phased array antenna is an electronically steerable phased array antenna. The electronically steerable phased array antenna has full electronic steering capability and is more compact and lower profile than a comparable mechanically steered antenna. The main drawback of fully electronic steering is that the antenna usually requires the integration of numerous expensive analog RF electronic components which may prohibitively raise the cost for commercial applications.
In a typical prior art embodiment, a phased array antenna comprises a radiating element that communicates dual linear signals to a hybrid coupler with either a 90° or a 180° phase shift and then through low noise amplifiers (LNA). Furthermore, the dual linear signals are adjusted by phase shifters before passing through a power combiner.
In the prior art, a typical digital phase shifter uses a switched delay line that is physically large and operates over a narrow band of frequencies due to its distributed nature. Another typical digital phase shifter implements a switched high-pass low-pass filter architecture, which has better operating bandwidth compared to a switched delay line but is still physically large. Also, the phase shifter is often made on gallium arsenide (GaAs). Though other materials may be used, GaAs is a higher quality material designed and controlled to provide good performance of electronic devices. However, in addition to being a higher quality material than other possible materials, GaAs is also more expensive and more difficult to manufacture. The typical phased array components take up a lot of area on the GaAs, resulting in higher costs. Furthermore, a standard phase shifter has high RF power loss, which is typically about n+1 dB of loss, where n is the number of phase bits in the phase shifter. Another prior art embodiment uses RF MEMS switches and has lower power loss but still consumes similar space and is generally incompatible with monolithic solutions. Furthermore, the typical components in a phased array antenna are distributed components that are frequency sensitive and designed for specific frequency bands.
Quadrature hybrids or other differential phase generating hybrids are used in a variety of RF applications, including phased array antennas. For example, quadrature hybrids are used for generating a circular polarization signals, power combining, or power splitting. Generally, the outputs of a quadrature hybrid have equal amplitude and a 90° phase difference. The quadrature hybrid is often implemented as a distributed structure, such as a Lange coupler, a branchline coupler, or a ring hybrid. Other RF hybrids, such as a magic tee or a ring hybrid, result in 180° phase shift, in general, an RF hybrid uses distributed components, limited in frequency band and requires significant physical space inversely proportional to an operating frequency. Moreover, the quadrature hybrid is typically made of GaAs and has associated RF power loss on the order of 3-4 dB per hybrid when used as a power splitter.
An in-phase hybrid may be configured as a power combiner or power splitter in a variety of RF applications, including phased array antennas. In an exemplary embodiment, the outputs of an in-phase hybrid have equal amplitude and a substantially zero differential phase difference. in another exemplary embodiment, the inputs of an in-phase hybrid configured as a power combiner encounter substantially zero differential phase and amplitude summation of the two input signals. In a typical embodiment of a power combiner, the in-phase hybrid is implemented as a distributed structure such as a Wilkinson hybrid. In general, an in-phase hybrid is limited in frequency band and requires significant physical space that is inversely proportional to the operating frequency, Like the quadrature hybrid, the in-phase hybrid is typically made on GaAs. Moreover, the in-phase hybrid generally has associated RF power loss on the order of 3-4 dB per hybrid when used as a power splitter and an associated RF power loss of about 1 dB when used as a power combiner.
Thus, a need exists for a phased array antenna architecture that is not frequency limited or polarization specific. Furthermore, the antenna architecture should he able to be manufactured on a variety of materials and with little or no associated RF power loss. Also, a need exists for a phased array antenna that uses less space than a similar capability prior art architecture, and is suitable for a monolithic implementation.
In an exemplary embodiment, a phased array solid-state architecture has dual-polarized feeds and is manufactured, for example, on highly flexible silicon germanium (SiGe). The implementation of dual-polarized feeds facilitates the operation of phased arrays where the polarization can be statically or dynamically controlled on a subarray or element basis. in an exemplary embodiment, the sub-component control is configured to optimize a performance characteristic associated with polarization, such as phase or amplitude adjustment.
An active phased array architecture may replace traditional distributed and GaAs implementations for the necessary functions required to operate electronically steerable phased array antennas. The architecture combines active versions of vector generators, power splitters, power combiners, and RF hybrids in a novel fashion to realize a fully or substantially monolithic solution for a wide range of antenna applications that can be realized with radiating elements having single-polarized or dual-polarized feeds.
In accordance with an exemplary embodiment, a phased array antenna is in communication with a radiating element, and the phased array antenna comprises a 90° hybrid configured to receive dual linearly polarized RF signals from the radiating element, a first vector generator, and a second vector generator. The 90° hybrid is configured to inject a 90° phase shift and generate a RHCP intermediate signal and a LHCP intermediate signal. The first vector generator is configured to receive the RHCP intermediate signal, phase adjust the RHCP intermediate signal for beam steering, and output a first RF signal. The second vector generator configured to receive the LHCP intermediate signal, phase adjust the LHCP intermediate signal for beam steering, and output a second RF signal.
In an exemplary embodiment, a phased array antenna is in communication with a radiating element, and the phased array antenna comprises a first vector generator, a second vector generator, and a hybrid. The first vector generator is configured to receive a first signal from the radiating element, provide phase and amplitude adjustment of the first signal for polarization tracking and beam steering, and output a first intermediate signal. The second vector generator is configured to receive a second signal from the radiating element, provide phase and amplitude adjustment of the second signal for polarization tracking and beam steering, and output a second intermediate signal. The hybrid is configured to receive the first intermediate signal and the second intermediate signal and generate two RF output signals with a phase difference. Furthermore, the two RF output signals are each a composite of the first intermediate signal and the second intermediate signal.
In another exemplary embodiment, a phased array antenna is in communication with a radiating element, and the phased array antenna comprises a first vector generator, a second vector generator, and a combiner. The first vector generator is configured to receive a first signal from the radiating element, provide phase and amplitude adjustment of the first signal for polarization tracking and beam steering, and to output a first intermediate signal. The second vector generator is configured to receive a second signal from the radiating element, provide phase and amplitude adjustment of the second signal for polarization tracking and beam steering, and to output a second intermediate signal. The combiner is configured to receive the first intermediate signal and the second intermediate signal, and combine the two signals into an RF output signal.
In yet another exemplary embodiment, a phased array antenna is in communication with a radiating element, and the phased array antenna comprises a hybrid, a first vector generator, a second vector generator, and a combiner. The hybrid is configured to receive dual linearly polarized RF signals from the radiating element, inject a phase shift, and generate a MCP intermediate signal and a LHCP intermediate signal. The first vector generator is configured to receive the RHCP intermediate signal, phase adjust the RHCP intermediate signal for beam steering, and output a first RF intermediate signal. The second vector generator is configured to receive the LHCP intermediate signal, phase adjust the LCHP intermediate signal for beam steering, and output a second RF intermediate signal. Furthermore, in the exemplary embodiment, the combiner is configured to receive the first RF intermediate signal and the second RIF intermediate signal, and combine the two signals into an RF output signal.
Furthermore, in an exemplary embodiment, a phased array antenna is in communication with a radiating element, and the phased array antenna comprises a hybrid, a first vector generator, a second vector generator, and an output hybrid. The hybrid is configured to receive dual linearly polarized RF signals from the radiating element, inject a phase shift, and generate a RHCP intermediate signal and a LHCP intermediate signal. The first vector generator is configured to receive the RHCP intermediate signal, phase adjust the RHCP intermediate signal for beam steering, and output a first RF intermediate signal. The second vector generator is configured to receive the LHCP intermediate signal, phase adjust the LHCP intermediate signal for beam steering, and output a second RF intermediate signal. Furthermore, the output hybrid is configured to receive the first RF intermediate signal and the second RF intermediate signal and generate two RF output signals with a phase difference. The two RF output signals are a composite of the first and second RF intermediate signals.
FIG. 1 illustrates an exemplary embodiment of an active power splitter;
FIG. 2 illustrates an exemplary embodiment of an active power combiner;
FIG. 3 illustrates an exemplary embodiment of an active RF hybrid;
FIG. 4 illustrates an exemplary embodiment of an active vector generator;
FIG. 5 illustrates an exemplary embodiment of an active antenna signal polarizer;
FIG. 6 illustrates an exemplary embodiment of a phased array antenna comprising an active combiner and configured for phase adjustment;
FIG. 7 illustrates an exemplary embodiment of a phased array antenna comprising a passive power combiner and configured for phase adjustment;
FIG. 8 illustrates an exemplary embodiment of a phased array antenna comprising an active RF hybrid configured for 90° operation and an active combiner, the phased array antenna being configured for phase adjustment;
FIG. 9 illustrates an exemplary embodiment of a phased array antenna comprising an active RF hybrid configured for 180° operation and an active combiner, the phased array antenna being configured for phase adjustment;
FIG. 10 illustrates an exemplary embodiment of a phased array antenna comprising an active RF hybrid configured for 90° operation and a passive power combiner, the phased array antenna being configured for phase adjustment;
FIG. 11 illustrates an exemplary embodiment of a phased array antenna comprising an active RF hybrid configured for 180° operation and a passive power combiner, the phased array antenna being configured for phase adjustment;
FIG. 12 illustrates an exemplary embodiment of a phased array antenna comprising a passive 90° hybrid and an active combiner and configured for phase adjustment;
FIG. 13 illustrates an exemplary embodiment of a phased array antenna comprising a passive 180° hybrid and an active combiner and configured for phase adjustment;
FIG. 14 illustrates an exemplary embodiment of a phased array antenna comprising a passive 90° hybrid and a passive power combiner and configured for phase adjustment;
FIG. 15 illustrates an exemplary embodiment of a phased array antenna comprising a passive 180° hybrid and a passive power combiner and configured for phase adjustment;
FIG. 16 illustrates an exemplary embodiment of a phased array antenna comprising an active RF hybrid and configured for phase adjustment;
FIG. 17 illustrates an exemplary embodiment of a phased array antenna comprising a passive hybrid and configured for phase adjustment;
FIG. 18 illustrates an exemplary embodiment of a phased array antenna comprising two active RF hybrids and configured for phase adjustment;
FIG. 19 illustrates an exemplary embodiment of a phased array antenna comprising an active RF hybrid and a passive hybrid and configured for phase adjustment;
FIG. 20 illustrates an exemplary embodiment of a phased array antenna comprising an active RF hybrid and a passive hybrid and configured for phase adjustment;
FIG. 21 illustrates an exemplary embodiment of a phased array antenna comprising two passive hybrids and configured for phase adjustment;
FIG. 22 illustrates an exemplary embodiment of a phased array antenna comprising an active. RF hybrid and configured for phase adjustment;
FIG. 23 illustrates an exemplary embodiment of a phased array antenna comprising a passive hybrid and configured for phase adjustment; and
FIG. 24 illustrates an exemplary embodiment of a multi-beam architecture.
While exemplary embodiments are described herein in sufficient detail to enable those skilled in the art to practice the invention, it should be understood that other embodiments may be realized and that logical material, electrical, and mechanical changes may be made without departing from the spirit and scope of the invention. Thus, the following detailed description is presented for purposes of illustration only.
A phased array antenna generally comprises multiple radiating elements, with each radiating element having a polarization component. in an exemplary embodiment, the radiating element has spatially orthogonal linear polarizations, spatially and electrically orthogonal circular polarizations, or spatially orthogonal and electrically non-orthogonal elliptical polarizations.
The polarization component of each radiating element may have one or more signals fed to the ports. In an exemplary embodiment, each radiating element has two feed ports and results in an unbalanced feed system. In yet another exemplary embodiment, each radiating element has three feed ports and results in a partially balanced feed system. In another exemplary embodiment, each radiating element has four feed ports and results in a fully balanced feed system.
In an exemplary embodiment, a phased array antenna with two feed ports is configured to generate and control different polarizations. Exemplary polarization states include a single circular polarization state, a single elliptical polarization state, a single linear polarization state, and two orthogonal polarization states.
The radiating elements may be in communication with an RF integrated circuit (RFIC). In an exemplary embodiment, the RFIC is configured to divide, alter, and re-mix the component RF signal to produce or detect various polarization states. For receiver applications, the RE signal corresponding to the detected polarization state in the RFIC may additionally be combined in a beam-forming network of the array. Conversely, for transmitter applications, the RFIC can receive input signals from a beam-forming network of the array and produce any desired polarization state.
In an exemplary embodiment, a phased array antenna comprises various components. The various components may include a vector generator, an active power splitter, an active power combiner, an active RE hybrid, or the like.
Active Splitter: FIG. 1 illustrates a schematic of an exemplary active power splitter. In an exemplary embodiment, an active power splitter 100 comprises a differential input subcircuit 110, a first differential output suhcircuit 120, and a second differential output subcircuit 1300 The differential input subcircuit 110 has paired transistors 111, 112 with a common emitter node and is constant current biased, as is typical in a differential amplifier. An input signal is communicated to the base of paired transistors 111, 112 in the differential input subcircuit 110. Both the first and second differential output subcircuits 120, 130 comprise a pair of transistors with a common base node and each common base is connected to ground.
The first differential output subcircuit 120 has a first transistor 121 emitter connected to the collector of one of the input subcircuit transistors 112. The emitter of the second output subcircuit transistor 122 is connected to the collector of the other input subcircuit transistor 111. In the exemplary embodiment, the first output is drawn from the collectors of transistors 121, 122 of the first differential output subcircuit 120. Furthermore, the second differential output subcircuit 130 is similarly connected, except the transistor 131, 132 emitters are inversely connected to the input subcircuit transistor 111, 112 collectors with respect to transistors 121, 122.
By inverting the input subcircuit transistor collector connections between the first and second differential output subcircuits, the first output and the second output are approximately 180° out of phase with each other. In another exemplary embodiment, transistor 131, 132 emitters are non-inversely connected to input subcircuit transistor 111, 112 collectors, causing the first output and the second output to be approximately in phase with each other. In general, the absolute phase shift of the output signals through the power splitter is not as important as the relative phasing between the first and second output signals.
In an exemplary embodiment, active power splitter 100 converts an input RF signal into two output signals. The output signal levels may be equal in amplitude, though this is not required. For a prior art passive power splitter, each output signal would be about 3 dB lower in power than the input signal. In contrast, an exemplary active splitter, such as active power splitter 100, can provide gain and the relative power level between the input signal and the output signal is adjustable and can he selectively designed. In an exemplary embodiment, the output signal is configured to achieve a substantially neutral or positive power gain over the input signal. For example, the output signal may achieve a 3 dB signal power gain over the input signal. In an exemplary embodiment, the output signal may achieve a power gain in the 0 dB to 5 dB range. Moreover, the output signal may be configured to achieve any suitable power gain.
In accordance with an exemplary embodiment, active power splitter 100 produces output signals with a differential phase between the two signals that is zero or substantially zero. The absolute phase shift of output signals through the active power splitter may not be as important as the differential phasing between the output signals.
In another exemplary embodiment, active power splitter 100 additionally provides matched impedances at the input and output ports. The matched impedances may be 50 ohms, 75 ohms, or other suitable impedances. Furthermore, in an exemplary embodiment, active splitter 100 provides isolation between the output ports of the active power splitter. In one exemplary embodiment, active power splitter 100 is manufactured as a MMIC with a compact size that is independent of the operating frequency due to a lack of distributed components.
Active Combiner: In an exemplary embodiment and with reference to FIG. 2, an active power combiner 200 comprises a first differential input subcircuit 210, a second differential input subcircuit 220, a single ended output subcircuit 230, and a differential output subcircuit 240, Each differential input subcircuit 210, 220 includes two pairs of transistors, with each transistor of each differential input subcircuit 210, 220 having a common emitter node with constant current biasing, as is typical in a differential amplifier.
A first input signal is communicated to the bases of the transistors in first differential input subcircuit 210. For example, a first line of input signal In1 is provided to one transistor of each transistor pair in first differential input subcircuit 210, and a second line of input signal In1 is provided to the other transistor of each transistor pair. Similarly, a second input signal is communicated to the bases of the transistors in second differential input subcircuit 220. For example, a first line of input signal In2 is provided to one transistor of each transistor pair in first differential input subcircuit 220, and a second line of input signal In2 is provided to the other transistor of each transistor pair. Furthermore, in an exemplary embodiment, a differential output signal is formed by a combination of signals from collectors of transistors in first and second differential input subcircuits 210, 220.
In an exemplary embodiment, active power combiner 200 converts two input RF signals into a single output signal. The output signal can either be a single ended output at single ended output subcircuit 230, or a differential output at differential output subcircuit 240. In other words, active power combiner 200 performs a function that is the inverse of active power splitter 100. The input signal levels can be of arbitrary amplitude and phase. Similar to an active power splitter, active power combiner 200 can provide gain and the relative power level between the inputs and output is also adjustable and can be selectively designed. In an exemplary embodiment, the output signal achieves a substantially neutral or positive signal power gain over the input signal, For example, the output signal may achieve a 3 dB power gain over the sum of the input signals. In an exemplary embodiment, the output signal may achieve a power gain in the 0 dB to 5 d13 range. Moreover, the output signal may achieve any suitable power gain.
In an exemplary embodiment, active power combiner 200 additionally provides matched impedances at the input and output ports. The matched impedances may be 50 ohms, 75 ohms, or other suitable impedances. Furthermore, in an exemplary embodiment, active power combiner 200 provides isolation between the input ports of the power combiner.
In yet another exemplary embodiment, the active power combiner 200 implements identical building block components as used in an exemplary active phased array architecture. In one exemplary embodiment, the active power combiner 200 is manufactured as a MMIC with a compact size that is independent of the operating frequency due to a lack of distributed components. Throughout, the active power combiner described in various exemplary embodiments may be similar to the active power combiner described with reference to FIGS. 6, 8-9, and 12-13.
Active RE Hybrid: In an exemplary embodiment, and with reference to FIG. 3, an active RF hybrid 300 comprises a first active power splitter 310, a second active power splitter 311, a first vector generator 320, a second vector generator 321, a first active power combiner 330, a second active power combiner 331, a first digital-to-analog converter (DAC) 340 and a second DAC 341. In accordance with the exemplary embodiment, first active power splitter 310 receives an input at Port I and communicates the input to first vector generator 320 and second active power combiner 331. Likewise, second active power splitter 311 receives an input at Port 2 and communicates the input to second vector generator 321 and first active power combiner 330. Vector generators 320, 321 are controlled in part by respective DACs 340, 341. In an exemplary embodiment, a 4-bit DAC is used but any number of bits many be used.
Furthermore, the output of first vector generator 320 is communicated to first active power combiner 330, and the output of second vector generator 321 is communicated to second active power combiner 331. in the exemplary embodiment, first active power combiner 330 receives input from first vector generator 320 and second active power splitter 311, and outputs a signal to Port 3. Similarly, second active power combiner 331 receives input from second vector generator 321 and first active power splitter 310, and outputs a signal to Port 4.
Active RF hybrid 300 may be used to replace various distributed components, such as a branch line coupler, Lange coupler, directional coupler, or 180° hybrid. In accordance with an exemplary embodiment, an active RF hybrid provides similar functionality in comparison to a traditional distributed hybrid. For example, active RF hybrid 300 may be dynamically configured to have variable phase differences between the output ports, which could be 90°, 180°, or some other phase difference. Another example is that active RF hybrid 300 provides port-to-port isolation and matched impedances at the input/output ports. Additional information regarding active RF hybrids is disclosed in the U.S. patent application Ser. No. 12/759,043, entitled “ACTIVE HYBRIDS FOR ANTENNA SYSTEMS”, filed Apr. 13, 2010, which is hereby incorporated by reference.
Furthermore, the active RF hybrid 300 has various advantages over a traditional passive distributed hybrid. In an exemplary embodiment, the active RF hybrid 300 does not result in a loss of power, but instead has a gain or is at least gain neutral. in another exemplary embodiment, the active RE hybrid 300 does not rely on distributed elements and is capable of operating over very wide bandwidths. In yet another exemplary embodiment, the active RE hybrid 300 implements identical building block components as used in an exemplary active phased array architecture. in one exemplary embodiment, the active RE hybrid 300 is manufactured as a MMIC with a compact size that is independent of the operating frequency due to a lack of distributed components.
Throughout, the active RF hybrid described in various exemplary embodiments may be similar to the active RF hybrid described with reference to FIGS. 8-11, 16, 18-20, and 22.
Vector Generator: In an exemplary embodiment, a vector generator converts an RF input signal into an output signal (sometimes referred to as an output vector) that is shifted in phase and/or amplitude to a desired level. This replaces the function of a typical phase shifter and adds the capability of amplitude control. In other words, a vector generator is a magnitude and phase control circuit. In the exemplary embodiment, the vector generator accomplishes this function by feeding the RF input signal into a quadrature network resulting in two output signals that differ in phase by about 90°. The two output signals are fed into parallel quadrant select circuits, and then through parallel variable gain amplifiers (VGAs). In an exemplary embodiment, the quadrant select circuits receive commands and may be configured to either pass the output signals with no additional relative phase shift between them or invert either or both of the output signals by an additional 180°. In this fashion, all four possible quadrants of the 360° continuum are available to both orthogonal signals. The resulting composite output signals from the current summer are modulated in at least one of amplitude and phase.
In accordance with an exemplary embodiment and with reference to FIG. 4, a vector generator 400 comprises a passive I/Q generator 410, a first variable gain amplifier (VGA) 420 and a second VGA 421, a first quadrant select 430 and a second quadrant select 431 each configured for phase inversion switching, and a current summer 440. The first quadrant select 430 is in communication with I/Q generator 410 and first VGA 420. The second quadrant select 431 is in communication with I/Q generator 410 and second VGA 421. Furthermore, in an exemplary embodiment, vector generator 400 comprises a digital controller 45( )that controls a first digital-to-analog converter (DAC) 460 and a second DAC 461. The first and second DACs 460, 461 control first and second VGAs 421, 420, respectively. Additionally, digital controller 450 controls first and second quadrant selects 430, 431.
In an exemplary embodiment, vector generator 400 controls the phase and amplitude of an RF signal by splitting the RF signal into two separate vectors, the in-phase (I) vector and the quadrature-phase (Q) vector. In one embodiment, the RF signal is communicated differentially. The differential RF signal communication may be throughout vector generator 400 or limited to various portions of vector generator 400. in another exemplary embodiment, the RF signals are communicated non differentially. The I vector and Q vector are processed in parallel, each passing through the phase inverting switching performed by first and second quadrant selects 430, 431. The resultant outputs of the phase inverting switches comprise four possible signals: a non-inverted I, an inverted I, a non-inverted Q, and an inverted Q. In this manner, all four quadrants of a phasor diagram are available for further processing by VGAs 420, 421. In an exemplary embodiment, two of the four possible signals non-inverted I, inverted I, non-inverted Q, and inverted Q are processed respectively through VGAs 420, 421, until the two selected signals are combined in current summer 440 to form a composite RF signal. The current summer 440 outputs the composite RF signal with phase and amplitude adjustments. In an exemplary embodiment, the composite RF signal is in differential signal form. In another exemplary embodiment, the composite RF signals are in single-ended form.
In an exemplary embodiment, control for the quadrant shifting and VGA functions is provided by a pair of DACs. In an exemplary embodiment, reconfiguration of digital controller 450 allows the number of phase bits to be digitally controlled after vector generator 400 is fabricated if adequate DAC resolution and automatic gain control (AUC) dynamic range exists. In an exemplary embodiment with adequate DAC resolution and AGC dynamic range, any desired vector phase and amplitude can be produced with selectable fine quantization steps using digital control, in another exemplary embodiment, reconfiguration of DACs 460, 461 can be made after vector generator 400 is fabricated in order to facilitate adjustment of the vector amplitudes.
Phased Array Architectures
In accordance with an exemplary embodiment, a phased array antenna comprises active components manufactured on silicon germanium (SiGe) in a monolithic solution. Other materials may be used, such as GaAs, silicon, or other suitable materials now known or hereinafter devised. A monolithic SiGe embodiment using active components results in certain advantages over the distributed/passive network in the prior art, including lower cost, smaller physical size that is independent of operating frequency, wider operating bandwidths, and the ability to provide power gain rather than a power loss.
Additionally, other advantages over the prior art embodiments are possible, depending on the phased array architecture. Some of the advantages include extensive system flexibility and very compact antenna systems because no distributed structures are required. Furthermore, some embodiments employ differential signaling to improve signal isolation when the RF signal is in analog form.
Some of the main advantages include that RF signals undergo a neutral or slight positive power gain when being communicated through the antenna system, rather than power losses that occur in the passive prior art systems. Another advantage is that the antenna system is not band limited, in other words, the antenna system is applicable to all frequency bands, including X, K Ku, Ka, and Q bands. In an exemplary embodiment, the antenna system operates over specific frequency ranges, such as 2-20 GHz, 20-40 GHz, or 30-45 GHz. In an exemplary embodiment, multi-band antennas are a practical option as a product.
Reconfigurability of the antenna system is also an advantage. In an exemplary embodiment, the antenna system includes the ability to reconfigure the number of phase bits in a DAC over full product life. In another exemplary embodiment, the antenna system is able to reconfigure the amplitude taper of the system over full product life. In yet another exemplary embodiment, the antenna system is able to reconfigure the system polarization over full product life. In an exemplary embodiment with adequate DAC resolution and AGC dynamic range, any arbitrary vector phase and amplitude can be produced with arbitrarily fine quantization steps using digital control,
Throughout, the vector generator described in various exemplary embodiments may be similar to the vector generator described with reference to FIGS. 5-24.
Active Antenna Polarizer: in accordance with an exemplary embodiment, an active antenna polarizer comprises a monolithic, digitally controlled active implementation for processing an RF signal. Two output RF signals communicate with a single radiating element and are digitally controlled, to provide any desired polarization phase or amplitude to the radiating element. In an exemplary embodiment, the active antenna polarizer comprises active components and results in no power loss in the communicated signals. Furthermore, in another exemplary embodiment, the active antenna polarizer is configured to operate over multiple frequency bands.
In an exemplary embodiment, and with reference to FIG. 5, a transmit active antenna polarizer 500 comprises an active power splitter 510, two vector generators 520, 521, and two DACs 530, 531. An input signal is actively split and transmitted through two vector generators 520, 521 in parallel. The vector generators 520, 521 are controlled by DACs 530, 531, and each vector generator produces a linear output signal. These two linear outputs are then used to energize the two spatially orthogonal feed ports of a radiating element (not shown). In another exemplary embodiment, the feeds to the radiating element can be differential in nature resulting in four feeds to the radiating element. In yet another exemplary embodiment, one of the feeds to the radiating elements can be differential while the other remains single ended in nature resulting in three feeds to the radiating element.
The transmit active antenna polarizer 500 may be considered a basic transmit embodiment which is configured to be implemented in a variety of different phased array antenna architectures. In an exemplary embodiment, the basic transmit embodiment is used in any frequency band and with different polarizations. For example, and as described below, the basic transmit embodiment may be used as the basis for phased array antenna transmitting in linear polarization, circular polarization, or elliptical polarization. In accordance with an exemplary embodiment, in order to operate in these different polarizations, vector generators 520, 521 control. the phase of the antenna signal.
In an exemplary embodiment, reconfiguration of DACs 530, 531 allows the number of phase bits to be digitally controlled after transmit active antenna polarizer 500 is fabricated if adequate DAC resolution and AGC dynamic range exists, in an exemplary embodiment with adequate DAC resolution and AGC dynamic range, any desired vector phase and amplitude can be produced with arbitrarily fine quantization steps using digital control. In another exemplary embodiment, DACs 530, 531 may be operationally reconfigured after transmit active antenna polarizer 500 is fabricated in order to facilitate adjustment of the signal amplitudes.
A receive active antenna polarizer (not shown) may be considered a basic receive embodiment which is configured to be implemented in a variety of different phased array antenna architectures. In an exemplary embodiment, the basic receive embodiment is used in any frequency band and with different polarizations. For example, and as described below, the basic receive embodiment may be used as the basis for phased array antenna receiving in linear polarization, circular polarization, or elliptical polarization. In accordance with an exemplary embodiment, in order to operate in these different polarizations, the vector generators control the phase of the antenna signal as described herein.
Described below are various specific phased array antenna system embodiments. The embodiments vary in terms of architecture, use of passive or active components, and whether differential or non-differential signaling is implemented. Though the exemplary embodiments of a phased array architecture are described in terms of a receive architecture, similar architectures could be implemented for transmitting signals in a phased array antenna. For example, RF power splitters would replace RF power combiners in the embodiments to facilitate the transmission of an RF signal.
In one exemplary embodiment, a combiner is in communication with two vector generators. The combiner may be either active or passive (see FIGS. 6 and 7). In an exemplary embodiment and with reference to FIG. 6, a phased array antenna 600 comprises an active combiner 610, two vector generators 620, 621, and two DACs 630, 631. A radiating element 601 is in communication with phased array antenna 600. Two spatially orthogonal feed ports of radiating element 601 transmit two input signals to vector generators 620, 621. The input signals are communicated through the two vector generators 620, 621 in parallel and actively summed to generate an RF output signal. The input signals may be linear, right-hand circular, left-hand circular, or elliptically polarized. The linear input signals may also be vertical and horizontal polarized. Vector generators 620, 621 enables phased array antenna 600 to have two degrees of freedom to allow the desired polarization to be detected and beam steering to be accomplished. In an exemplary embodiment, vector generator 620 may be used for beam steering while vector generator 621 offsets the phase of vector generator 620 by ±90 degrees to provide detection of RHCP signals or LHCP signals. Similar embodiments allow for the beam steering and polarization tracking of elliptically polarized signals as well.
Passive components may also be implemented in phased array antennas. In an exemplary embodiment, and with reference to FIG. 7, a phased array antenna 700 comprises a passive power combiner 710, two vector generators 720, 721, and two DACs 730, 731, input signals are communicated through two vector generators 720, 721 in parallel and passively combined at passive power combiner 710 to generate an RF output signal. In one embodiment, passive power combiner 710 may be a Wilkinson power divider configured to combine the two vector generator outputs. In another embodiment, passive power combiner 710 may be any suitable power combiner now known or herein after devised. The input signals may be linear, right-hand circular, left-hand circular, or elliptically polarized. The linear input signals may also be vertical and horizontal polarized. Furthermore, phased array antenna 700 is capable of beam steering as described with respect to phased array antenna 600.
In an exemplary embodiment, an RF hybrid is combined with two parallel vector generators and a combiner. The addition of an RF hybrid enables detection of LHCP and RHCP signals simultaneously. The combiner can be either active or passive. Similarly, the hybrid can be active or passive. Furthermore, the hybrid may be a 90° hybrid or a 180° hybrid. FIG. 8 illustrates an exemplary phased array antenna 800 comprising an active RF hybrid 810 with a 90° phase shift, two vector generators 820, 821, two DACs 830, 831, and an active combiner 840. The output signal is a composite of the two input signals.
Similarly, FIG. 9 illustrates an exemplary phased array antenna 900 comprising an active RF hybrid 910 with a 180° phase shift, two vector generators 920, 921, two DACs 930, 931, and an active combiner 940. In one embodiment, the two outputs of the 180° active RF hybrid 910 have a 90° phase difference. More specifically, the two outputs are +/−45° phase slanted from the inputs of the active RF hybrid 910. The output signal is a composite of the two input signals.
In an exemplary embodiment and with reference to FIG. 10, a phased array antenna 1000 comprises a 90° active RF hybrid 1010, two vector generators 1020, 1021, two DACs 1030, 1031, and a passive power combiner 1040. This embodiment and the components are similar to the embodiment in FIG. 8, except the passive power combiner 1040 is implemented instead of an active power combiner. The output signal is a composite of the two input signals. Moreover, phased array antenna 1000 has higher loss and narrower bandwidth compared to phased array antenna 800.
As previously mentioned, the active hybrid could also be implemented as a 180° active hybrid. In an exemplary embodiment and with reference to FIG. 11, a phased array antenna 1100 comprises a 180° active RF hybrid 1110, two vector generators 1120, 1121, two DACs 1130, 1131, and a passive power combiner 1140. As an example, passive power combiner 1140 may be a Wilkinson power divider. In another embodiment, passive power combiner 1140 may be any suitable power combiner now known or herein after devised. In one embodiment, the two outputs of active RF hybrid 1110 have a 90° phase difference. More specifically, the two outputs are +/−45° phase slanted from the inputs of active RF hybrid 1110. In an exemplary embodiment, the two outputs of active RF hybrid 1110 may be any combination of phase slants that result in a 90° phase difference. The output signal is a composite of the two input signals.
In addition to passive combiners, a hybrid may also be a passive component. FIG. 12 illustrates a phased array antenna 1200 comprising a 90° passive hybrid 1210, two vector generators 1220, 1221, two DACs 1230, 1231, and an active combiner 1240. The output signals of 90° passive hybrid 1210 may be a right-hand circular, a left-hand circular, or elliptically polarized signal. The 90° passive hybrid 1210 may, for example, be a branchline coupler or a Lange coupler. The output signals of 90° passive hybrid 1210 are each a composite of the two input signals received from a radiating element. The main difference between 90° passive hybrid 1210 and 90° active RF hybrid 1010 is the size of the components, with 90° active RF hybrid 1010 being substantially smaller, in addition to the various advantages of active components as previously described.
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Patent InfoApplication # US 20120299775 A1Publish Date 11/29/2012 Document # 13540394 File Date 07/02/2012 USPTO Class 342372 Other USPTO Classes International Class 01Q3/00 Drawings 25 Follow us on Twitter@FreshPatents
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