Source: https://patents.google.com/patent/EP1657783A2/en
Timestamp: 2018-10-16 22:10:52
Document Index: 147467239

Matched Legal Cases: ['Application No. 2000', 'Art 1', 'arts 703', 'arts 703', 'arts 703', 'arts 703', 'art 703', 'arts 703', 'Art 1']

EP1657783A2 - Antenna control unit and phased-array antenna - Google Patents
EP1657783A2
EP1657783A2 EP20050027572 EP05027572A EP1657783A2 EP 1657783 A2 EP1657783 A2 EP 1657783A2 EP 20050027572 EP20050027572 EP 20050027572 EP 05027572 A EP05027572 A EP 05027572A EP 1657783 A2 EP1657783 A2 EP 1657783A2
EP20050027572
EP1657783B1 (en )
EP1657783A3 (en )
As shown in figure 1, a paraelectric transmission line layer 102 and a ferroelectric transmission line layer 105 are laminated through a ground conductor 107, and plural phase shifters which are connected via through holes 108 that pass through the ground conductor 107 are disposed on both of the transmission line layers at some positions on a feeding line that branches off from the input terminal between all antenna terminals and an input terminal to which a high-frequency power is applied. In addition, loss elements each having the same transmission loss amount as the phase shifter, or the phase shifters are disposed so that transmission loss amounts from all of the antenna terminals to the input terminal are equalized.
Accordingly, an antenna control unit which can be manufactured in fewer manufacturing processes and has a pointed beam and a large beam tilt amount, and a phased-array antenna that employs such antenna control unit can be obtained.
Systems such as "Active phased-array antenna and antenna control unit" described in Japanese Published Patent Application No. 2000-236207 (hereinafter, referred to as Prior Art 1) have been suggested as examples of conventional phased-array antennas that employ a ferroelectric as a phase shifter.
Initially, with reference to figures 9, operating principles of a conventional phase shifter are described. Figures 9 are diagrams illustrating a phase shifter that is suggested in the conventional phased-array antenna. Figure 9(a) is a diagram illustrating a construction of the phase shifter, and figure 9(b) is a diagram showing permittivity changing characteristics of a ferroelectric material.
Further, two linear conductor layers 704a1 and 704a2 are disposed on the ferroelectric base material 702 so as to be located on extension lines of two opposed linear parts 703a1 and 703a2 of the rectangular loop-shaped conductor layer 703a and linked to one ends of the two linear parts 703a1 and 703a2, respectively. These two linear conductor layers 704a1 and 704a2 and the ferroelectric base material 702 form the microstrip stub 704.
Further, conductor layers 715a and 720a are disposed on the paraelectric base material 701 so as to be located on extension lines of the two linear parts 703a1 and 703a2 and linked to the other ends of the two linear parts 703a1 and 703a2, respectively.
Here, the one end and the other end of the linear part 703a1 on the loop-shaped conductor layer 703a are ports 2 and 1 of the microstrip hybrid coupler 703, respectively. On the other hand, the one end and the other end of the linear parts 703a2 of the loop-shaped conductor layer 703a are ports 3 and 4 of the microstrip hybrid coupler 703, respectively.
Hereinafter, a detailed explanation will be given. In the phase shifter 700 having such a construction that one reflection element (microstrip stub 704) is connected to the adjacent two ports (ports 2 and 3) of the properly-designed microstrip hybrid coupler 703, a high-frequency power that enters from the input port (port 1) is not outputted from the input port 1 but the high-frequency power upon which a power reflected from the reflection element has been reflected is outputted only from the output port (port 4). In the reflection from the microstrip stub 704 as the reflection element, a bias field 705 that is produced by the control voltage is in the same direction as that of a field produced by the high-frequency power that passes through the microstrip stub 704, as shown in figure 9(a). Therefore, as shown in figure 9(b), when the control voltage is changed, an effective permittivity of the microstrip stub 704 with respect to the high-frequency power varies adaptively. Accordingly, the equivalent electrical length of the microstrip stub 704 for the high-frequency power varies, and the phase on the microstrip stub 704 is changed.
The conventional phased-array antenna 830 comprises plural antenna elements 806a-806d which are placed in a row at regular intervals on a dielectric base material, an antenna control unit 800, and a beam tilt voltage 820. The antenna control unit 800 comprises a feeding terminal 808 to which a high-frequency power is applied (hereinafter, referred to as an input terminal), a high frequency blocking element 809, and plural phase shifters 807a1-807a4.
In this conventional phased-array antenna 830, the antenna element 806a is connected to the input terminal 808, the antenna element 806b is connected to the input terminal 808 through one phase shifter 807a1, the antenna element 806c is connected to the input terminal 808 through two phase shifters 807a3 and 807a4, and the antenna element 806d is connected to the input terminal 808 through three phase shifters 807a2, 807a3, and 807a4, by means of a feeding line (hereinafter, referred to as a transmission line), respectively. The beam tilt voltage 820 is connected to the input terminal 808 through the high frequency blocking element 809.
It is assumed here that each construction of the phase shifters 807a1-807a4 is the same as that described with reference to figure 9, and the phase shifters 807a1-807a4 have the same characteristics.
In the phased-array antenna 830 having the above construction, the number of phase shifters 807 which are located between one of the antenna elements 806a-806d and the input terminal 808 is one larger than the number of phase shifters 807 which are located between the adjacent antenna element 806 and the input terminal 808, respectively, and further, all of the phase shifters 807 have the same characteristics. Therefore, as shown in figure 10(b), the control of the antenna's directivity (beam tilt) is performed by one beam tilt voltage 820.
The control of the antenna directivity will be described in more detail. For example, assuming that each of the phase shifters 807a1-807a4 delays the phase of the high-frequency power that passes through each phase shifter by a phase shift amount Φ and the adjacent phase shifters 807 are spaced by a distance d, respectively, the high-frequency power that has entered the antenna element 806a is supplied to the input terminal 808 with no phase change, as shown in figure 10(a). In contrast to this, the high-frequency power that has entered the antenna element 806b is supplied to the input terminal 808, with its phase being delayed by the phase shifter 807a1 by a phase shift amount Φ. The high-frequency power that has entered the antenna element 806c is supplied to the input terminal 808, with its phase being delayed by the phase shifters 807a3 and 807a4, by a phase shift amount 2Φ. Further, the high-frequency power that has entered the antenna element 806d is supplied to the input terminal 808, with its phase being delayed by the phase shifters 807a2, 807a3, and 807a4, by a phase shift amount 3Φ.
In other words, a direction of the maximum sensitivity for radio waves received by the antenna elements 806a-806d is a direction D that forms a predetermined angle Θ (Θ=cos-1(Φ/d)) with respect to the direction of the row of the antenna elements 806a-806d. It is assumed here that references w1 to w3 in figure 10(a) denote planes of the received waves in the same phase, respectively.
However, in the conventional phased-array antenna 803 having the above-mentioned construction, the numbers of phase shifters 807 which are located between the respective antenna elements 806 and the input terminal 808 are different, and further there are transmission losses in the respective phase shifters 807. Therefore, the effects of combining powers from the respective antenna elements 806a-806d are decreased, so that the shape of the beam that is shown in figure 10(b) is deformed, whereby it is difficult to obtain a pointed beam (large directivity gain), as well as the amount of beam tilt is reduced, and accordingly the control of the antenna's directivity is deteriorated.
Further, as described with reference to figure 9(a), each of the phase shifters 807 that are used for the conventional phased-array antenna 830 is formed in one piece, by allocating areas on the same plane to the ferroelectric base material 702 and the paraelectric base material 701 which constitute the phase shifter 700, respectively. Therefore, a distributed capacitance Cn per unit length of the line for the microstrip hybrid coupler 703 and a distributed capacitance Cf per unit length of the line for the microstrip stub 704 are greatly different from each other. Accordingly, high-frequency power reflection is produced at the connection between the microstrip hybrid coupler 703 and the microstrip stub 704, whereby the power from the microstrip hybrid coupler 703 does not enter the microstrip stub 704 so efficiently, and consequently the sufficient phase shift amount cannot be obtained.
Hereinafter, a detailed explanation will be given. For, example, the line impedance Z is generally expressed by the distributed inductance L per unit length of the line and the distributed capacitance C per unit length of the line as Z"2 (the square of Z) = L/C. Further, when it is assumed that all fields exist only within the base material, and all of the fields are approximated to be linear and perpendicular to the ground conductor, the distributed capacitance C per unit length of the line is expressed by the line width W, the base material thickness H, and the base material permittivity ε, as C = ε W/H. When the distributed capacitance Cn per unit length of the line for the microstrip hybrid coupler 703 and the distributed capacitance Cf per unit length of the line for the microstrip stub 704 are compared with each other by utilizing the above-mentioned expressions, assuming that the permittivity of the paraelectric base material 701 as the base material of the microstrip hybrid coupler 703 is ε n and the permittivity of the ferroelectric base material 702 as the base material of the microstrip stub 704 is ε f, the relationship εn « εf is generally established. Further, since the line widths W of the microstrip hybrid coupler 703 and the microstrip stub 704, and the distances H of the respective conductors are the same, the distributed capacitance Cn per unit length of the line for the microstrip hybrid coupler 703 (= ε nW/H) and the distributed capacitance Cf per unit length of the line for the microstrip stub 704 (=εfW/H) are greatly different. Consequently, as mentioned above, the power from the microstrip hybrid coupler 703 does not enter the microstrip stub 704 so efficiently, and thus the sufficient phase shift amount cannot be obtained.
The present invention is made to solve the above-mentioned problems, and this invention has for its object to provide an antenna control unit that can be manufactured in fewer manufacturing processes (low cost), and has a pointed beam (large directivity gain) and a large amount of beam tilt, and a phased-array antenna that employs such an antenna control unit.
According to Claim 5 of the present invention, there is provided an antenna control unit including: a feeding terminal to which a high-frequency power is applied; a feeding line that branches off into m lines at a k-th stage branch from the feeding terminal when m = 2^k (k-th power of 2) (m, k is an integer); m antenna terminals for connecting antenna elements, which are provided on ends of the m feeding lines and arranged in a row, said antenna terminals being referred to as first, second, ... , and m-th antenna terminals, respectively; Mk phase shifters (Mk = M(k-1) x 2 + 2^(k-1) when k≧1 and M1=1) which all have the same characteristics and electrically change a phase of a high-frequency signal that passes through the feeding line; and Mk loss elements which all have the same characteristics and have a transmission loss amount that is equal to a transmission loss amount of the phase shifter, in which the phase shifters are placed at some positions on the feeding line that branches off into m lines, such that the number of phase shifters which are located between a (n+1)-th antenna terminal (n is an integer that is from 1 to m-1) and the feeding terminal is one larger than the number of phase shifters which are located between an n-th antenna terminal and the feeding terminal, and the loss elements are placed at some positions on the feeding line that branches off into m lines, such that the transmission loss amount from the n-th antenna terminal to the feeding terminal is larger than the transmission loss amount from the (n+1)-th antenna terminal to the feeding terminal, by a transmission loss amount corresponding to one phase shifter.
According to Claim 6 of the present invention, there is provided an antenna control unit including: a feeding terminal to which a high-frequency power is applied; a feeding line that branches off into m lines at a k-th stage branch from the feeding terminal when m = 2^k (k-th power of 2) (m, k is an integer); m antenna terminals for connecting antenna elements, which are provided on ends of the m feeding lines and arranged in a row, said antenna terminals being referred to as first, second, ..., and m-th antenna terminals, respectively; Mk positive beam tilting phase shifters (Mk = M(k-1) x 2 + 2^(k-1) when k≧1 and M1=1) which all have the same characteristics and electrically change a phase of a high-frequency signal that passes through the feeding line in a positive direction; and Mk negative beam tilting phase shifters which all have the same characteristics and electrically change the phase of the high-frequency signal that passes through the feeding line in a negative direction, in which the positive beam tilting phase shifters are placed at some positions on the feeding line that branches off into m lines, such that the number of the positive beam tilting phase shifters which are located between an (n+1)-th antenna terminal (n is an integer from 1 to m-1) and the feeding terminal is one larger than the number of the positive beam tilting phase shifters which are located between an n-th antenna terminal to the feeding terminal, and the negative beam tilting phase shifters are placed at some positions on the feeding line that branches off into m lines, such that the number of negative beam tilting phase shifters which are located between an n-th antenna terminal to the feeding terminal is one larger than the number of negative beam tilting phase shifters which are located between an (n+1)-th antenna terminal to the feeding terminal.
According to Claim 7 of the present invention, there is provided a two-dimensional antenna control unit including: m 2 row antenna control units and one column antenna control unit, this row antenna control unit being the antenna control unit of Claim 5 including m = m 1 antenna terminals (m 1 is an integer), and this column antenna control unit being the antenna control unit of Claim 5 including m = m 2 antenna terminals (m 2 is an integer), in which feeding terminals of the m 2 row antenna control units are connected to the m 2 antenna terminals of the column antenna control unit, respectively.
According to Claim 8 of the present invention, there is provided a two-dimensional antenna control unit including: m 2 row antenna control units and one column antenna control unit, this row antenna control unit being the antenna control unit of Claim 6 including m = m 1 antenna terminals (m 1 is an integer), and this column antenna control unit being the antenna control unit of Claim 6 including m = m 2 antenna terminals (m 2 is an integer), in which feeding terminals of the m 2 row antenna control units are connected to the m 2 antenna terminals of the column antenna control unit, respectively.
Figures 1 are a perspective view (figure 1(a)) and a cross-sectional view (figure 1(b)) illustrating a construction of a phase shifter according to a first embodiment of the present invention, which is employed for a phased-array antenna.
Figures 2 are a perspective view (figure 2(a)) and a cross-sectional view (figure 2(b)) illustrating a construction of a phase shifter according to a second embodiment of the present invention, which is employed for a phased-array antenna.
Figures 3 are a diagram illustrating a construction of a phased-array antenna according to a third embodiment of the present invention (figure 3(a)), and a diagram showing directivities of this phased-array antenna (figure 3(b)).
Figures 4 are a diagram illustrating a construction of a phased-array antenna according to a fourth embodiment of the present invention (figure 4(a)), and a diagram showing directivities of this phased-array antenna (figure 4(b)).
Figure 5 is a diagram illustrating a construction of a phased-array antenna according to a fifth embodiment of the present invention.
Figure 7 is a table showing the relationship of the number of branch stages (k), the number of antenna elements (m), and the number of phase shifters (Mk) in the antenna control unit or phased-array antenna according to the sixth embodiment.
Figures 8 are diagrams showing placements of phase shifters when k=1 and m=2 (figure 8(a)), when k=2 and m=4 (figure 8(b)), and when k=3 and m=8 (figure 8(c)).
Figures 9 are a diagram illustrating a construction of a phase shifter that is employed for a conventional phased-array antenna (figure 9(a)), and a diagram showing permittivity changing characteristics of a ferroelectric material (figure 9(b)).
Figures 10 are a diagram showing a construction and operating principles of the conventional phased-array antenna (figure 10(a)), and a diagram showing directivities of the conventional phased-array antenna (figure 10(b)).
Hereinafter, a first embodiment of the present invention will be described with reference to figure 1.
In figures 1, reference numeral 100 denotes a phase shifter. Numeral 101 denotes a paraelectric base material, numeral 102 denotes a paraelectric transmission line layer, numeral 103 denotes a microstrip hybrid coupler, numeral 104 denotes a ferroelectric base material, numeral 105 denotes a ferroelectric transmission line layer, numeral 106 denotes a microstrip stub, numeral 107 denotes a ground conductor, and numeral 108 denotes a through hole by which the microstrip hybrid coupler 103 and the microstrip stub 106 are connected through the ground conductor 107.
Thus, in the phase shifter 100 of the first embodiment, as shown in figure 1(a), the microstrip hybrid coupler 103 is formed on the paraelectric transmission line layer 102 that employs a paraelectric material for the base material 101, the microstrip stub 106 is formed on the ferroelectric transmission line layer 105 that employs a ferroelectric material for the base material 104, these two transmission line layers 102 and 105 are laminated through the ground conductor 107, and then the microstrip hybrid coupler 103 and the microstrip stub 106 are connected via through holes 108 which pass through the ground conductor 107. Further, as shown in figure 1(b), the distance Hf between conductors that constitute the transmission line of the ferroelectric conductor line layer 103 is larger than the distance Hn between conductors that constitute the transmission line of the paraelectric transmission line layer 102. Accordingly, the line impedances Z of the microstrip hybrid coupler 103 and the microstrip stub 106 can be matched, whereby the phase shifter 100 providing an effective phase shift amount can be manufactured in simpler manufacturing processes.
A detailed explanation of the phase shifter will be given hereinafter. For example, assuming that the permittivity of the paraelectric base material 101 as the base material for the microstrip hybrid coupler 103 is ε n, and the permittivity of the ferroelectric base material 104 as the base material for the microstrip stub 106 is ε f, the distributed capacitance Cn per unit length of the line for the microstrip hybrid coupler 103 is given by an expression Cn = ε n · W/Hn, and the distributed capacitance Cf per unit length of the line for the microstrip stub 106 is given by an expression Cf = ε f · W/Hf. When Cn and Cf are compared with each other, the relationship En « E f is established as described above, but the relationship Hn < Hf is established as shown in figure 1(b), so that the difference between the distributed capacitance Cn per unit length of the line for the microstrip hybrid coupler 103 and the distributed capacitance Cf per unit length of the line for the microstrip stub 106 gets smaller. Consequently, the reduction in the matching degree between the line impedances Z of the microstrip hybrid coupler 103 and the microstrip stub 106 can be avoided, so that the power from the microstrip hybrid coupler 103 enters the microstrip stub 106 efficiently, whereby a sufficient phase shift amount can be obtained.
In other words, the base material of the phase shifter 100 is composed of the paraelectric base material 101, the ground conductor 107, and the ferroelectric base material 104. A rectangular loop-shaped conductor layer 103a is disposed on the paraelectric base material 101, and this loop-shaped conductor layer 103a and the paraelectric base material 101 form the microstrip hybrid coupler 103.
Under the ferroelectric base material 104, two linear conductor layers 106a1 and 106a2 are placed so as to be linked to one end of the two opposed linear portions 103a1 and 103a2 of the rectangular loop-shaped conductor layer 103a via the through holes 108, respectively. These two linear conductor layers 106a1 and 106a2 and the ferroelectric base material 104 form the microstrip stub 106.
On the paraelectric base material 101, conductor layers 115a and 120a are disposed so as to be located on extension lines of the two linear portions 103a1 and 103a2, and linked to the other ends of the two linear portions 103a1 and 103a2, respectively.
This conductor layer 115a and the paraelectric base material 101 form an input line 115, and the conductor layer 120a and the paraelectric base material 101 form an output line 120. Here, the one end and the other end of the linear portion 103a1 of the loop-shaped conductor layer 103a are ports 2 and 1 of the microstrip hybrid coupler 103, respectively, and the one end and the other end of the linear portion 103a2 of the loop-shaped conductor layer 103a are ports 3 and 4 of the microstrip hybrid coupler 103, respectively.
A second embodiment of the present invention will be described with reference to figures 2.
Figures 2 are a perspective view (figure 2(a)) and a cross-sectional view (figure 2(b)) illustrating a construction of the phase shifter according to the second embodiment, which is employed for the phased-array antenna of the present invention.
In figures 2, reference numeral 200 denotes a phase shifter. Numeral 201 denotes a paraelectric base material, numeral 202 denotes a paraelectric transmission line layer, numeral 203 denotes a microstrip hybrid coupler, numeral 204 denotes a ferroelectric base material, numeral 205 denotes a ferroelectric transmission line layer, numeral 206 denotes a microstrip stub, numeral 207 denotes a ground conductor, and numeral 208 denotes a coupling window that is formed in the ground conductor 207, for electromagnetically coupling the microstrip hybrid coupler 203 and the microstrip stub 206.
As described in the first embodiment, when a magnetic material is added to the microstrip stub 704 of the conventional phase shifter 700 shown in figure 9(a) to increase the distributed inductance L per unit length of the line as shown in Prior Art 1, so as to solve the problem that a sufficient amount of phase shift for the conventional phase shifter 700 is not obtained, the conventional phase shifter 700 that is formed in one piece by allocating areas on the same plane to the ferroelectric base material 702 and the paraelectric base material 701, respectively, needs much more processes, whereby the manufacturing cost is increased.
In the phase shifter 200 according to the second embodiment as shown in figure 2 (a), the microstrip hybrid coupler 203 is formed on the paraelectric transmission line layer 202 that uses a paraelectric material for the base material 201, and the microstrip stub 206 is formed on the ferroelectric transmission line layer 205 that uses a ferroelectric material for the base material 204, then these two transmission line layers 202 and 205 are laminated through the ground conductor 207, and the microstrip hybrid coupler 203 and the microstrip stub 206 are electromagnetically connected via the coupling window 208 that is formed in the ground conductor 207, and further, as shown in figure 2(b), the distance Hf between conductors that form the transmission line on the ferroelectric transmission line layer 205 is larger than the distance Hn between conductors that form the transmission line on the paraelectric transmission line layer 202. Accordingly, the line impedances Z of the microstrip hybrid coupler 203 and the microstrip stub 206 can be matched, whereby the phase shifter 200 providing an effective phase shift amount can be manufactured in simpler manufacturing processes.
Hereinafter, a detailed explanation will be given. For example, assuming that the permittivity of the paraelectric base material 201 as the base material of the microstrip hybrid coupler 203 is ε n and the permittivity of the ferroelectric base material 204 as the base material of the microstrip stub 206 is ε f, the distributed capacitance Cn per unit length of the line for the microstrip hybrid coupler 203 is given by an expression Cn = ε n · W/Hn, and the distributed capacitance Cf per unit length of the line for the microstrip stub 206 is given by an expression Cf = ε f · W/Hf. When Cn and Cf are compared with each other, ε n << ε f but in this second embodiment Hn < Hf as shown in figure 2(b), so that the difference between the distributed capacitance Cn per unit length of the line for the microstrip hybrid coupler 203 and the distributed capacitance Cf per unit length of the line for the microstrip stub 206 gets smaller. Consequently, the deterioration of the matching between the line impedances Z of the microstrip hybrid coupler 203 and the microstrip stub 206 can be avoided, whereby the power from the microstrip hybrid coupler 203 enters the microstrip stub 206 efficiently, and a sufficient phase shift amount can be obtained.
In other words, the base material of the phase shifter 200 is composed of the paraelectric base material 201, the ground conductor 207, and the ferroelectric base material 204. A rectangular loop-shaped conductor layer 203a is disposed on the paraelectric base material 201, and this loop-shaped conductor layer 203a and the paraelectric base material 201 form the microstrip hybrid coupler 203.
Two linear conductor layers 206a1 and 206a2 are disposed under the ferroelectric base material 204 so as to be electromagnetically connected to one end of the two opposed linear portions 203a1 and 203a2 of the rectangular loop-shaped conductor layer 203a, respectively, via the coupling window 208. These two linear conductor layers 206a1 and 206a2 and the ferroelectric base material 204 form the microstrip stub 206.
Further, conductor layers 215a and 220a are disposed on the paraelectric base material 201 so as to be located on extension lines of the two linear portions 203a1 and 203a2 and linked to the other ends of the two linear portions 203a1 and 203a2, respectively.
This conductor layer 215a and the paraelectric base material 201 form an input line 215, and the conductor layer 220a and the paraelectric base material 201 form an output line 220. Here, the one end and the other end of the linear portion 203a1 of the loop-shaped conductor layer 203a are ports 2 and 1 of the microstrip hybrid coupler 203, and the one end and the other end of the linear portion 203a2 of the loop-shaped conductor layer 203a are ports 3 and 4 of the microstrip hybrid coupler 203, respectively.
In figure 3(a), a phased-array antenna 330 according to the third embodiment comprises an antenna control unit 300, a beam tilt voltage 320 for performing control of the directivity (beam tilt) as shown in figure 3(b), and four antenna elements 310a-310d. The antenna control unit 300 comprises an input terminal (feeding terminal) 301, four antenna terminals 307a-307d, four phase shifters 308a1-308a4, four loss elements 309a1-309a4, high frequency blocking element 311, a DC blocking element 312, a transmission line (feeding line) 302 from the input terminal 301, two transmission lines 304a and 304b that branch off at a first branch 303, and four transmission lines 306a-306d that branch off from the transmission lines 304a and 304b at second branches 305a and 305b.
The antenna control unit 300 according to the third embodiment includes one input terminal 301, then the transmission line 302 from the input terminal 301 branches off into two transmission lines 304a and 304b at the first branch 303, and further the two transmission lines 304a and 304b that branch off at the first branch 303 further branch off into two transmission lines at the second branches 305a and 305b, whereby branched four transmission lines 306a-306d are obtained.
When the four antenna terminals 307a-307d are arranged in a row, which are referred to as first, second, third, and fourth antenna terminals, respectively, and when it is assumed that n is an integer that satisfies 0 < n < 4, the phase shifters 308a1-308a4 are arranged so that the number of phase shifters 308a which are located between the (n+1)-th antenna terminal 307 and the input terminal 301 is one larger than the number of phase shifters 308a which are located between the n-th antenna terminal 307 and the input terminal 301. Here, the respective phase shifters 308a1-308a4 have the same characteristics.
Further, in the antenna control unit 300 according to the third embodiment, the loss elements 309a1-309a4 each having a transmission loss that is equal to a transmission loss amount corresponding to one phase shifter 308a are placed so that the number of loss elements 309a which are located between the n-th antenna terminal 307 and the input terminal 301 is one larger than the number of loss elements 309a which are located between the (n+1)-th antenna terminal 307 and the input terminal 301. Therefore, the transmission loss amounts from all the antenna terminals 307a-307d to the input terminal 301 are of the same value.
In common phased-array antennas, when the transmission loss amounts from the respective antenna elements 310a-310d to the input terminal 301 as a power composition point are different from each other, the power compositing effect is reduced, whereby the shape of the beam as shown in figure 3(b) is deformed and it becomes difficult to obtain a pointed beam (large directivity gain), as well as the beam tilt amount is reduced, and accordingly the control of the antenna's directivity is deteriorated.
However, in the antenna control unit 300 according to the third embodiment, the loss elements 309a are placed so that the amount of transmission loss which occurs from the n-th antenna terminal 307 (n is an integer that satisfies 0 < n < 4) to the input terminal 301 is larger than the transmission loss amount from the (n+1)-th antenna terminal 307 to the input terminal 301, by an amount as much as the transmission loss corresponding to one phase shifter 308a. Therefore, the transmission loss amounts from all the antenna elements 310a-310d to the input terminal 301 are of the same value, whereby a phased-array antenna that has a pointed beam and a satisfactory beam tilt amount can be realized.
As described above, according to the third embodiment, when n is an integer that satisfies 0 < n < 4, the phase shifters 308a are placed such that the number of phase shifters 308a which are located between the (n+1)-th antenna terminal 307 and the input terminal 301 is one larger than the number of phase shifters 308a which are located between the n-th antenna terminal 307 and the input terminal 301, and further the loss elements 309a are placed such that the transmission loss amount from the n-th antenna terminal 307 to the input terminal 301 is larger than the transmission loss amount from the (n+1) - th antenna terminal 307 to the input terminal 301, by an amount as much as the transmission loss corresponding to one phase shifter 308a. Therefore, even when any passage loss is generated in the phase shifters 308a1-308a4, the amounts of distributed power for the respective antenna elements 310a-310d are not different from each other, and consequently, the antenna control unit 300 by which the beam shape is not deformed or the changes in the beam direction are not reduced can be obtained. Further, when this antenna control unit 300 is employed for a phased-array antenna, the transmission loss amounts from all of the antenna elements 310a-310d to the input terminal 301 can be made equal, whereby a phased-array antenna that has a pointed beam and a satisfactory beam tilt amount can be realized.
Figure 4(a) is a diagram illustrating a construction of a phased-array antenna according to the fourth embodiment, and figure 4(b) is a diagram showing directivities of the phased-array antenna according to the fourth embodiment in a case where a beam tilt voltage is applied and a case where the beam tilt voltage is not applied.
In figure 4(a), a phased-array antenna 430 according to the fourth embodiment comprises an antenna control unit 400, negative and positive beam tilt voltages 421 and 422 that perform control on negative and positive directivities (beam tilt), respectively, as shown in figure 4(b), and four antenna elements 410a-410d. The antenna control unit 400 comprises an input terminal 401, four antenna terminals 407a-407d, four positive beam tilting phase shifters 408a1-408a4, four negative beam tilting phase shifters 408b1-408b4, high frequency blocking elements 411a-411f, DC blocking elements 412a-412f, a transmission line 402 from the input terminal 401, two transmission lines 404a and 404b that branch off at a first branch 403, and four transmission lines 406a-406d that branch off from the transmission lines 404a and 404b at second branches 405a and 405b.
Each of the two transmission lines 404a and 404b that branch off at the first branch 403 is provided with one DC blocking element 412, and further each of the four transmission lines 406a-406d that branch off at the second branches 405a and 405b, respectively, is provided with one DC blocking element 412. A high frequency block element 411 is placed on one end of the respective negative beam tilting phase shifters 408b1, 408b4, and, 408b2, and on one end of the respective positive beam tilting phase shifters 408a1, 408a4, and 408a2.
The four transmission lines 406a-406d are provided with four antenna terminals 407a-407d, respectively, so as to be connected to four antenna elements 410a-410d.
These four antenna terminals 407a-407d, which are referred to as first, second, third, and fourth antenna terminals, respectively, are arranged in a row, and when assuming that n is an integer that satisfies 0 < n < 4, the positive beam tilting phase shifters 408a1-408a4 are placed so that the number of phase shifters which are located from the (n+1)-th antenna terminal 407 to the input terminal 401 is one larger than the number of phase shifters which are located from the n-th antenna terminal 407 to the input terminal 401.
Further, the negative beam tilting phase shifters 408b1-408b4 are placed so that the number of phase shifters which are located between the n-th antenna terminal 407 and the input terminal 401 is one larger than the number of phase shifters which are located between the (n+1)-th antenna terminal 407 and the input terminal 401.
Here, the positive beam tilting phase shifters 408a1-408a4 and negative beam tilting phase shifters 408b1-408b4 all have the same characteristics (same transmission loss amount).
In common phased-array antennas, when the transmission loss amounts from the respective antenna elements 410a-410d to the input terminal 401 as the electric power composition point are different from each other, the electric power composition effect is reduced, whereby the shape of beam as shown in figure 4 (b) is deformed, and thus it is difficult to obtain a pointed beam (large directivity gain), as well as the beam tilt amount is reduced, and accordingly the control on the antenna's directivity is deteriorated.
As described above, according to the fourth embodiment, when n is an integer that satisfies 0 < n < 4, the positive beam tilting phase shifters 408a1-408a4 are placed so that the number of positive beam tilting phase shifters 408a which are located between the (n+1)-th antenna terminal 407 and the input terminal 401 is one larger than the number of positive beam tilting phase shifters 408a which are located between the n-th antenna terminal 407 and the input terminal 401, and further the negative beam tilting phase shifters 408b1-408b4 are placed so that the number of negative beam tilting phase shifters 408b which are located between the n-th antenna terminal 407 and the input terminal 401 is one larger than the number of negative beam tilting phase shifters 408b which are located between the (n+1)-th antenna terminal 407 and the input terminal 401. Therefore, each of the phase shifters 408 takes charge of only a smaller phase shift amount, and consequently, an antenna control unit 400 which does not reduce the beam tilt amount even when the permittivity change rate for the ferroelectric material of each phase shifter 408 is low can be obtained. Further, when the antenna control unit 400 is employed, the transmission loss amounts from all the antenna elements 410a-410d to the input terminal 401 can be equalized, whereby a phased-array antenna that has a more pointed beam and a more satisfactory beam tilt amount can be realized.
In figure 5, a phased-array antenna 530 according to the fifth embodiment comprises antenna elements 510a(1-4)-510d(1-4), X-axial antenna control units 500a1-500a4 that perform control of the X-axial directivity (beam tilt), a Y-axial antenna control unit 500b that performs control of the Y-axial directivity, an X-axial beam tilt voltage 520a, and a Y-axial beam tilt voltage 520b. Each of the X-axial antenna control units 500a includes antenna terminals 507a-507d, and an input terminal 501a. The Y-axial antenna control unit 500b includes antenna terminals 507a-507d, and an input terminal 501b. Here, it is assumed that each of the X-axial antenna control units 500a1-500a4 and the Y-axial antenna control unit 500b has the same construction as that of the antenna control unit 300 as described above in detail in the third embodiment.
The input terminals 501a1-501a4 of the X-axial antenna control units 500a1-500a4 are connected to the antenna terminals 507a-507d of the Y-axial antenna control unit 500b, respectively. Though not shown here, four phase shifters 308a and four loss elements 309a each having the same transmission loss amount are disposed in each of the X-axial antenna control units 500a1-500a4 and the Y-axial antenna control unit 500b as shown in figure 3, as described in the third embodiment.
Therefore, according to the phased-array antenna 530 of the fifth embodiment, the transmission loss amounts from all the antenna terminals 507a-507d to the input terminal 501a in the X-axial antenna control units 500a1-500a4 are of the same value, and further the transmission loss amounts from all the antenna terminals 507a-507d to the input terminal 501b in the Y-axial antenna control unit 500b are of the same value. Accordingly, a phased-array antenna that has a pointed beam (large directivity gain) and a satisfactory beam tilt amount, and can control the X-axial directivity and the Y-axial directivity can be realized.
As described above, the phased-array antenna of the fifth embodiment employs an antenna control unit which includes the X-axial antenna control units 500a1-500a4 that control the X-axial directivity and the Y-axial antenna control unit 500b that controls the Y-axial directivity, and as the X-axial and Y-axial antenna control units 500, an antenna control unit as described in the third embodiment, which is provided with the phase shifters 308a and the loss elements 309a as many as the phase shifters 308a, each loss element having the same transmission loss amount as the phase shifter 308a, whereby the distributed power to the respective antenna elements 510 is equalized also when any passage loss occurs in the phase shifter 308, thereby to prevent the deformation of the beam shape or the reduction in the beam tilt changes. Therefore, a phased-array antenna that has a pointed beam (large directivity gain) and a satisfactory beam tilt amount, as well as can control the X-axial and Y-axial directivities can be realized.
A sixth embodiment of the present invention will be described with reference to figure 6.
In figure 6, a phased-array antenna 630 of the sixth embodiment includes antenna elements 610a(1-4)-610d(1-4), X-axial antenna control units 600a1-600a4 that perform control of the X-axial directivity (beam tilt), a Y-axial antenna control unit 600b that performs control of the Y-axial directivity, an X-axial negative beam tilt voltage 621a, an X-axial positive beam tilt voltage 622a, a Y-axial negative beam tilt voltage 621b, and a Y-axial positive beam tilt voltage 622b. Further, each of the X-axial antenna control units 600a includes antenna terminals 607a-607d, and an input terminal 601a. The Y-axial antenna control unit 600b includes antenna terminals 607a-607d, and the input terminal 601b. It is assumed here that each of the X-axial antenna control units 600a1-600a4 and the Y-axial antenna control unit 600b has the same construction as that of the antenna control unit 400 that has been specifically described in the fourth embodiment.
The input terminals 601a1-601a4 of the X-axial antenna control units 600a1-600a4 are connected to the antenna terminals 607a-607d of the Y-axial antenna control unit 600b, respectively. Though not shown here, four positive beam tilting phase shifters 408a and four negative beam tilting phase shifters 408b are included in each of the X-axial antenna control units 600a1-600a4 and the Y-axial antenna control unit 600b, as shown in figure 4, as described in the fourth embodiment.
Therefore, according to the phased-array antenna 630 of the sixth embodiment, in each of the X-axial antenna control units 600a1-600a4 and the Y-axial antenna control unit 600b, the transmission loss amounts from all the antenna terminals 607a-607d to the input terminal 601a are of the same value, and each phase shifter takes charge of only a smaller phase shift amount, whereby a phased-array antenna which has a more pointed beam and a more satisfactory beam tilt amount, as well as can control the X-axial and Y-axial directivities can be realized.
As described above, according to the sixth embodiment, the phased-array antenna includes the x-axial antenna control units 600a1-600a4 that control the X-axial directivity, and the Y-axial antenna control unit 600b that controls the Y-axial directivity. Further, as the X-axial and Y-axial antenna control units 600, an antenna control unit is employed in which equal numbers of positive beam tilting phase shifters 408a and negative beam tilting phase shifters 408b each having the same transmission loss amount are disposed as described in the fourth embodiment, and thus each of the phase shifters 408 takes charge of only a smaller phase shift amount even when the permittivity change rate of the ferroelectric material for each phase shifter 408 is low, thereby avoiding the reduction in the beam tilt amount, and further the distributed power to the respective antenna elements 610 are equalized even when the passage loss arises in each phase shifter, whereby the deformation of the beam shape or the reduction of changes in the beam direction can be prevented. Therefore, a phased-array antenna which has a more pointed beam and a more satisfactory beam tilt amount, and can control the X-axial and Y-axial directivities can be realized.
Further, while four antenna elements are employed in any of the above-mentioned embodiments, other number of antenna elements many be employed. For example, when a feeding line (transmission line) branches off into m lines through k branch stages from an input terminal to which a high-frequency power is applied (m = 2^k (k-th power of 2), (k is an integer)), only m pieces of antenna elements are required, and the number Mk of phase shifters that are then required can be given by the following expression: M k = M ( k − 1 ) × 2 + 2 ^ ( k − 1 ) ( when k ≧ 1 , M 1 = 1 )
Hereinafter, a detailed explanation will be given with reference to figures 7 and 8. Figure 7 is a diagram showing the relationship of the number of branch stages (k), the number of antenna elements (m), and the number of phase shifters (Mk) in the antenna control unit or phased-array antenna according to the sixth embodiment. Figures 8 are diagrams showing arrangement of phase shifters in a case where k=1 and m=2 in figure 7 (figure 8(a)), a case where k=2 and m=4 (figure 8(b)), and a case where k=3 and m=8 (figure 8(c)).
For example, when the number of branch stages k=3, the number m of antenna elements is m = 2^3 = 8 as shown in figure 7, and the number M3 of phase shifters is M3 = M2x2+2^2 = 12. The phase shifters in this case are arranged as shown in figure 8(c) such that the number of phase shifters which are located between the (n+1)-th antenna terminal (0 < n < 8) and the input terminal is one larger than the number of phase shifters which are located between the n-th antenna terminal and the input terminal. For the sake of simplifying the explanation, only Mk phase shifters are shown in figure 8, but in the antenna control unit 300 as described in the third embodiment and the phased-array antenna 330 that employs this antenna control unit 300, Mk loss elements as many as the phase shifters are further disposed as shown in figure 3. In the case of the antenna control unit 400 as described in the fourth embodiment and the phased-array antenna 430 that employs this antenna control unit 400, when the Mk phase shifters shown in this figure are positive beam tilting phase shifters, Mk negative beam tilting phase shifters are further disposed as shown in figure 4.
An antenna control unit (300) including:
a feeding terminal (301) to which a high-frequency power is applied;
a feeding line (302) that branches off into m lines at a k-th branch stage from the feeding terminal (301) when m =2^k (k-th power of 2) (m, k is an integer);
m antenna terminals (307a-307d) for connecting antenna elements (310a-310d), which are provided on ends of the m feeding lines and arranged in a row, said antenna terminals being referred to as first, second,..., and m-th antenna terminals, respectively;
Mk phase shifters (308a1-308a4) (Mk = M(k-1) x 2 +2^(k-1) when k ≥ 1 and M1 = 1) which all have the same characteristics and electrically change a phase of a high-frequency signal that passes through the feeding line; and
Mk loss elements (309a1-309a4) which all have the same characteristics and have a transmission loss amount that is equal to a transmission loss amount of the phase shifter, wherein
the phase shifters are placed at some positions on the feeding line that branches off into m lines, such that the number of phase shifters which are located between a(n+1)-th antenna terminal (n is an integer that is from 1 to m-1) and the feeding terminal is one larger than the number of phase shifters which are located between an n-th antenna terminal and the feeding terminal, and
An antenna control unit (400) including:
a feeding terminal (401) to which a high-frequency power is applied;
a feeding line (402) that branches off into m lines at a k-th branch stage from the feeding terminal when m =2^k (k-th power of 2) (m, k is an integer);
m antenna terminals (407a-407d) for connecting antenna elements (410a-410d), which are provided on ends of the m feeding lines and arranged in a row, said antenna terminals being referred to as first, second,..., and m-th antenna terminals, respectively;
Mk positive beam tilting phase shifters (408a1-408a4) (Mk = M(k-1) x 2 + 2^(k-1) when k ≥ 1 and M1 = 1) which all have the same characteristics and electrically change a phase of a high-frequency signal that passes through the feeding line in a positive direction; and
Mk negative beam tilting phase shifters (408b1-408b4) which all have the same characteristics and electrically change the phase of the high-frequency signal that passes through the feeding line in a negative direction, wherein
the positive beam tilting phase shifters are placed at some positions on the feeding line that branches off into m lines, such that the number of the positive beam tilting phase shifters which are located between an (n+1)-th antenna terminal (n is an integer from 1 to m-1) and the feeding terminal is one larger than the number of the positive beam tilting phase shifters which are located between an n-th antenna terminal to the feeding terminal, and
the negative beam tilting phase shifters are placed at some positions on the feeding line that branches off into m lines, such that the number of negative beam tilting phase shifters which are located between an n-th antenna terminal to the feeding terminal is one larger than the number of negative beam tilting phase shifters which are located between an (n+1) -th antenna terminal to the feeding terminal.
A two-dimensional antenna control unit including:
m2 row antenna control units and one column antenna control unit, said row antenna control unit being the antenna control unit of claim 1 including m = m1 antenna terminals(m1 is an integer), and
said column antenna control unit being the antenna control unit of claim 1 including m = m2 antenna terminals (m2 is an integer), wherein
m2 row antenna control units and one column antenna control unit, said row antenna control unit being the antenna control unit of claim 2 including m = m1 antenna terminals (m1 is an integer), and
said column antenna control unit being the antenna control unit of claim 2 including m = m2 antenna terminals (m2 is an integer), wherein
A phased-array antenna that includes, on a dielectric substrate: plural antenna elements; and an antenna control unit according to any of claims 1 to 4 having a feeding terminal to which a high-frequency power is applied, and phase shifters that are connected with the respective antenna elements by feeding lines which branch off from the feeding terminal and electrically change a phase of a high-frequency signal that passes through between the respective antenna elements and the feeding terminal, said phase shifters being placed at some positions on the feeding lines.
EP20050027572 2002-06-13 2003-06-13 Antenna control unit and phased-array antenna Expired - Fee Related EP1657783B1 (en)
EP20030733421 Division EP1512195B9 (en) 2002-06-13 2003-06-13 Antenna control unit and phased-array antenna
EP1657783A2 true true EP1657783A2 (en) 2006-05-17
EP1657783A3 true EP1657783A3 (en) 2006-05-31
EP1657783B1 EP1657783B1 (en) 2007-08-08
EP20030733421 Not-in-force EP1512195B9 (en) 2002-06-13 2003-06-13 Antenna control unit and phased-array antenna
EP20050027572 Expired - Fee Related EP1657783B1 (en) 2002-06-13 2003-06-13 Antenna control unit and phased-array antenna
DE (4) DE60315520D1 (en)
WO2003107480A2 (en) 2003-12-24 application
US5870066A (en) 1999-02-09 Chip antenna having multiple resonance frequencies
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