Source: http://patents.com/us-20170202106.html
Timestamp: 2017-07-22 12:58:39
Document Index: 800686868

Matched Legal Cases: ['Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 62', 'Application No. 62', 'Application No. 62']

Application # 2017/0202106. ENCLOSURE COOLING SYSTEM - Patents.com
20170202106
Bhutta; Imran Ahmed
In one embodiment, the invention can be a system for cooling an enclosure
enclosing electrical components and configured to prevent air and exhaust
from escaping the enclosure. The system can include a heat sink
comprising a heat exchanger, and a tube extending into and out of the
heat exchanger, the tube configured to transport liquid through the heat
exchanger. The system can further include a fan configured to push air
heated by electrical components onto the heat exchanger. The heat
exchanger can be configured to receive heat from air pushed by the fan,
and transfer the received heat to the liquid being transported by the
tube through the heat exchanger.
Bhutta; Imran Ahmed; (Moorestown, NJ)
Applicant: Name City State Country Type Reno Technologies, Inc. Wilmington DE US Family ID:
1000002539643
15/467667
Related U.S. Patent Documents Application NumberFiling DatePatent Number 14982244Dec 29, 2015 15467667 14935859Nov 9, 2015 14982244 14622879Feb 15, 2015 14935859 14616884Feb 9, 2015 14622879 14594262Jan 12, 20159496122 14616884 61925974Jan 10, 2014 61940139Feb 14, 2014 61940165Feb 14, 2014 62077753Nov 10, 2014 62097498Dec 29, 2014 62312070Mar 23, 2016 Current U.S. Class:
1/1 Current CPC Class: H05K 7/20218 20130101; H05K 7/20154 20130101; H03H 7/38 20130101; H01L 23/473 20130101; H01J 2237/334 20130101; H01J 37/3299 20130101; H01J 37/32577 20130101; H01L 21/67069 20130101; H01J 2237/332 20130101; H01J 37/32183 20130101
International Class: H05K 7/20 20060101 H05K007/20; H01L 23/473 20060101 H01L023/473; H01J 37/32 20060101 H01J037/32; H03H 7/38 20060101 H03H007/38
1. A system comprising: an enclosure enclosing electrical components and
configured to prevent air and exhaust from escaping the enclosure; a heat
sink at least partially within the enclosure, the heat sink comprising: a
heat exchanger; and a tube extending into and out of the heat exchanger,
the tube configured to transport liquid through the heat exchanger; and a
fan enclosed by the enclosure, the fan configured to push air heated by
electrical components onto the heat exchanger; wherein the heat exchanger
is configured to receive heat from air pushed by the fan, and transfer
the received heat to the liquid being transported by the tube through the
2. The system of claim 1 wherein the electrical components form part of a
system for manufacturing semiconductors.
5. The system of claim 1 wherein the fan is mounted on the heat sink.
6. The system of claim 1 wherein: the heat sink further comprises a main
housing adjacent the heat exchanger; the tube extends into and out of the
main housing; and the tube is further configured to transport liquid
through the main housing.
7. The system of claim 6 wherein the main housing comprises a main
housing surface configured to lay against a component shelf surface, the
component shelf surface comprising a thermally conductive material and
having a plurality of shelf electrical components.
10. The system of claim 6 wherein: the main housing has a first edge and
a second edge opposite the first edge; the heat exchanger has a first
edge and a second edge opposite the first edge, the main housing second
edge being adjacent the heat exchanger first edge; the tube enters the
main housing at the main housing first edge; the tube enters the heat
exchanger at the heat exchanger first edge; the tube exits the heat
exchanger at the heat exchanger first edge; and the tube exits the main
housing at the main housing first edge.
13. A method of cooling an enclosure enclosing electrical components and
configured to prevent air and exhaust from escaping the enclosure, the
method comprising: positioning a heat sink at least partially within the
enclosure, the heat sink comprising: a heat exchanger; and a tube
extending into and out of the heat exchanger, the tube configured to
transport liquid through the heat exchanger; by a fan enclosed by the
enclosure, pushing air heated by electrical components onto the heat
exchanger; receiving, at the heat exchanger, heat from the pushed air;
and transferring, by the heat exchanger, the received heat to liquid
being transported by the tube through the heat exchanger.
14. The method of claim 13 wherein the electrical components form part of
a system for manufacturing semiconductors.
15. The method of claim 13 wherein the electrical components form part of
an RF generator or an RF matching network.
16. The method of claim 15 further comprising, upon receipt of a fault
signal, removing power from inputs of the RF generator or the RF matching
17. The method of claim 15 further comprising, upon receipt of a fault
signal, opening a system interlock.
18. The method of claim 13 wherein the fan is mounted on the heat sink.
19. The method of claim 13 wherein: the heat sink further comprises a
main housing adjacent the heat exchanger; the tube extends into and out
of the main housing; and the tube transports liquid through the main
20. The method of claim 19 further comprising laying a main housing
surface against a component shelf surface, the component shelf surface
comprising a thermally conductive material and having a plurality of
shelf electrical components.
21. The method of claim 19 wherein the main housing comprises a main
housing surface configured to receive electrical components directly on
the main housing surface.
22. The method of claim 19 wherein the main housing and heat exchanger
are located side-by-side and contact each other along at least one edge.
23. The method of claim 19 wherein: the main housing has a first edge and
24. The method of claim 19 wherein the tube extends along a first side of
the main housing and a second side of the main housing opposite the first
25. The method of claim 19 wherein the main housing comprises a thermally
26. A method of manufacturing a semiconductor, the method comprising:
operably coupling a matching network between an RF source and a plasma
chamber, wherein the plasma chamber is configured to deposit a material
layer onto the substrate or etch a material layer from the substrate, and
electrical components of the RF source or the matching network are
enclosed by an enclosure that is configured to prevent air and exhaust
from escaping the enclosure; positioning a heat sink at least partially
within the enclosure, the heat sink comprising a heat exchanger and a
tube extending into and out of the heat exchanger, the tube configured to
transport liquid through the heat exchanger; placing a substrate in the
plasma chamber; energizing plasma within the plasma chamber by coupling
RF power from the RF source into the plasma chamber to perform a
deposition or etching; by a fan enclosed by the enclosure, pushing air
heated by electrical components onto the heat exchanger; receiving, at
the heat exchanger, heat from the pushed air; and transferring, by the
heat exchanger, the received heat to liquid being transported by the tube
through the heat exchanger.
27. A heat sink comprising: a heat exchanger; and a tube extending into
and out of the heat exchanger, the tube configured to transport liquid
through the heat exchanger; wherein heat exchanger is configured to
receive heat from air heated by electrical components, and transfer the
received heat to the liquid being transported by the tube through the
28-37. (canceled)
[0001] The present application is a continuation in part of U.S. patent
application Ser. No. 14/982,244, filed Dec. 29, 2015, which is a
continuation in part of U.S. patent application Ser. No. 14/935,859,
filed Nov. 9, 2015, which is a continuation in part of U.S. patent
application Ser. No. 14/622,879, filed Feb. 15, 2015, which is a
continuation in part of U.S. patent application Ser. No. 14/616,884,
filed Feb. 9, 2015, which is a continuation in part of U.S. patent
application Ser. No. 14/594,262, filed Jan. 12, 2015, now U.S. Pat. No.
9,496,122, which in turn claims priority to U.S. Provisional Patent
Application No. 61/925,974, filed Jan. 10, 2014. U.S. patent application
Ser. No. 14/616,884 also claims priority to U.S. Provisional Patent
Application No. 61/940,139, filed Feb. 14, 2014. U.S. patent application
Ser. No. 14/622,879 also claims priority to U.S. Provisional Patent
Application No. 61/940,165, filed Feb. 14, 2014. U.S. patent application
Ser. No. 14/935,859, filed Nov. 9, 2015, also claims the benefit of U.S.
Provisional Patent Application No. 62/077,753, filed Nov. 10, 2014. U.S.
patent application Ser. No. 14/982,244, filed Dec. 29, 2015, also claims
priority to U.S. Provisional Patent Application No. 62/097,498, filed
Dec. 29, 2014. The present application also claims the benefit of U.S.
Provisional Patent Application No. 62/312,070 filed on Mar. 23, 2016. The
disclosures of these references are incorporated herein by reference in
[0002] Radio Frequency (RF) amplifiers, generators and matching networks
are used in many applications, including telecommunication, broadcast,
and industrial processing. These systems and their components can
generate heat that can compromise system operation. Thus, there is a need
to cool such systems.
[0003] In an RF generator, for example, an RF signal is taken at the input
of the RF amplifier and this RF signal is used to modulate the power
derived from the DC power supply in order to provide RF power at
significantly higher power than the input. The difference between the RF
output power and the DC input power is the loss within the RF generator.
This loss is then dissipated as heat among the different components of
the RF generator. A fan can circulate air from the outside of the RF
housing into the housing and over the circuits and then purge the air
from holes in the sides of the housing. For higher power RF generators,
one could use a water-cooled heat sink that is situated adjacent to the
power Field Effect Transistors (FET) to remove heat generated in their
components. Some of the electrical circuits, however, are not mounted on
the heat sink and therefore must be cooled by other means, such as air
circulation that requires the use of fans in addition to the use of a
water-cooled heat sink.
[0004] Similarly, for an RF matching network, the internal resistances of
the components result in varying levels of heat generation in those
components. Certain components may be cooled efficiently when they are
mounted to a heat sink while other components can only be cooled through
air flowing over those components. The heat sink in an RF matching
network may be either air cooled or water cooled.
[0005] In a semiconductor manufacturing system, an RF generator delivers
power to a vacuum chamber, through an RF matching network, to create a
plasma. While the RF generator has internal protection circuitry that can
reduce the output power or completely shut off the power if a fault
occurs in the system, sometimes the reaction to a fault is not fast
enough and can result in a component failure. A component's failure can
result in thermal damage to the component as well as the PCB assembly or
other assemblies to which it is mounted. This thermal damage can result
in scorching of the component or other assemblies resulting in outgassing
of material from those assemblies. If the RF generator is air cooled and
has an air inlet and exhaust holes in its enclosure, the outgassed gasses
and material can be ejected from the RF generator and contaminate the
surrounding environment. Contamination of the surrounding environment can
in turn contaminate wafers or substrates in the semiconductor fabrication
plant (fab) resulting in extensive financial damage to the fab. A similar
situation can result from failure of a component or assembly in an
air-cooled RF matching network.
[0006] For these reasons, it is important to prevent the outgassing of
gasses and material from an RF generator or an RF matching network or a
combination an RF generator and an RF matching network. Additionally, to
limit further damage to the RF generator and or the RF matching network,
a need exists to limit or prevent further power from being dissipated
into the failed component. Thus, there exists a need for an effective
method for cooling enclosed systems, such as systems utilizing large
power generators.
[0007] The present disclosure may be directed, in one aspect, to a system
including an enclosure enclosing electrical components and configured to
prevent air and exhaust from escaping the enclosure; a heat sink at least
partially within the enclosure, the heat sink comprising a heat
exchanger; and a tube extending into and out of the heat exchanger, the
tube configured to transport liquid through the heat exchanger; and a fan
enclosed by the enclosure, the fan configured to push air heated by
[0008] In another aspect, a method of cooling an enclosure enclosing
electrical components and configured to prevent air and exhaust from
escaping the enclosure includes positioning a heat sink at least
tube configured to transport liquid through the heat exchanger; by a fan
enclosed by the enclosure, pushing air heated by electrical components
onto the heat exchanger; receiving, at the heat exchanger, heat from the
pushed air; and transferring, by the heat exchanger, the received heat to
liquid being transported by the tube through the heat exchanger.
[0009] In yet another aspect, a method of manufacturing a semiconductor
includes operably coupling a matching network between an RF source and a
plasma chamber, wherein the plasma chamber is configured to deposit a
material layer onto the substrate or etch a material layer from the
substrate, and electrical components of the RF source or the matching
network are enclosed by an enclosure that is configured to prevent air
and exhaust from escaping the enclosure; positioning a heat sink at least
partially within the enclosure, the heat sink comprising a heat exchanger
and a tube extending into and out of the heat exchanger, the tube
configured to transport liquid through the heat exchanger; placing a
substrate in the plasma chamber; energizing plasma within the plasma
chamber by coupling RF power from the RF source into the plasma chamber
to perform a deposition or etching; by a fan enclosed by the enclosure,
pushing air heated by electrical components onto the heat exchanger;
receiving, at the heat exchanger, heat from the pushed air; and
transferring, by the heat exchanger, the received heat to liquid being
transported by the tube through the heat exchanger.
[0010] In yet another aspect, a heat sink includes a heat exchanger; and a
transport liquid through the heat exchanger; wherein heat exchanger is
configured to receive heat from air heated by electrical components, and
transfer the received heat to the liquid being transported by the tube
[0011] The present disclosure will become more fully understood from the
[0012] FIG. 1 is a schematic representation of an embodiment of an RF
impedance matching network using EVCs incorporated into a semiconductor
wafer fabrication system;
[0013] FIG. 2A illustrates an EVC for use in an RF impedance matching
[0014] FIG. 2B is a schematic representation of an embodiment of an
electronic circuit for providing a variable capacitance.
[0015] FIG. 2C is a schematic representation of an embodiment of an EVC
having three capacitor arrays.
[0016] FIG. 3 illustrates a first switching circuit for use with an EVC;
[0017] FIG. 4 is a graphical representation showing the timing
capabilities of a driver circuit to switch to high voltage on the common
[0018] FIG. 5 is a graphical representation showing the timing
capabilities of a driver circuit to switch to low voltage on the common
[0019] FIG. 6A illustrates a second switching circuit for use with an EVC;
[0020] FIG. 6B illustrates a third switching circuit for use with an EVC;
[0021] FIG. 7 is a graph showing the capacitance range of an EVC;
[0022] FIG. 8 is a graph showing the stable delivered power and the low
reflected power that an impedance matching network including EVCs may
provide during tuning;
[0023] FIG. 9 is a graphical representation showing the reflected RF power
profile through an RF impedance matching network using EVCs and showing
the voltage supplied to the driver circuit for the EVCs; and
[0024] FIG. 10 is a flow chart showing an embodiment of a process for
matching an impedance.
[0025] FIG. 11 shows a cooling system according to one embodiment.
[0026] FIGS. 12-14 show views of a heat sink according to one embodiment.
[0027] FIG. 15 is a flow chart for a method of cooling an enclosure
according to one embodiment.
[0028] The following description of the preferred embodiment(s) is merely
exemplary in nature and is in no way intended to limit the invention or
inventions. The description of illustrative embodiments is intended to be
read in connection with the accompanying drawings, which are to be
considered part of the entire written description. In the description of
the exemplary embodiments disclosed herein, any reference to direction or
orientation is merely intended for convenience of description and is not
intended in any way to limit the scope of the present invention. Relative
terms such as "lower," "upper," "horizontal," "vertical," "above,"
"below," "up," "down," "left," "right," "top," "bottom," "front" and
"rear" as well as derivatives thereof (e.g., "horizontally,"
"downwardly," "upwardly," etc.) should be construed to refer to the
orientation as then described or as shown in the drawing under
discussion. These relative terms are for convenience of description only
and do not require that the apparatus be constructed or operated in a
particular orientation unless explicitly indicated as such. Terms such as
"attached," "affixed," "connected," "coupled," "interconnected,"
"secured" and other similar terms refer to a relationship wherein
structures are secured or attached to one another either directly or
indirectly through intervening structures, as well as both movable or
rigid attachments or relationships, unless expressly described otherwise.
The discussion herein describes and illustrates some possible
non-limiting combinations of features that may exist alone or in other
combinations of features. Furthermore, as used herein, the term "or" is
to be interpreted as a logical operator that results in true whenever one
or more of its operands are true. Furthermore, as used herein, the phrase
"based on" is to be interpreted as meaning "based at least in part on,"
and therefore is not limited to an interpretation of "based entirely on."
[0029] As used throughout, ranges are used as shorthand for describing
each and every value that is within the range. Any value within the range
can be selected as the terminus of the range. In addition, all references
cited herein are hereby incorporated by referenced in their entireties.
In the event of a conflict in a definition in the present disclosure and
that of a cited reference, the present disclosure controls.
[0030] Turning in detail to the drawings, FIG. 1 illustrates an RF
impedance matching network 11 having an RF input 13 connected to an RF
source 15 and an RF output 17 connected to a plasma chamber 19. An RF
input sensor 21 is connected between the RF impedance matching network 11
and the RF source 15 so that the RF signal output from the RF source 15
may be monitored. An RF output sensor 49 is connected between the RF
impedance matching network 11 and the plasma chamber 19 so that the RF
output from the impedance matching network, and the plasma impedance
presented by the plasma chamber 19, may be monitored. Certain embodiments
may include only one of the input sensor 21 and the output sensor 49. The
functioning of these sensors 21, 49 are described in greater detail
[0031] The RF impedance matching network 11 serves to help maximize the
amount of RF power transferred from the RF source 15 to the plasma
chamber 19 by matching the impedance at the RF input 13 to the fixed
impedance of the RF source 15. The matching network 11 can consist of a
single module within a single housing designed for electrical connection
to the RF source 15 and plasma chamber 19. In other embodiments, the
components of the matching network 11 can be located in different
housings, some components can be outside of the housing, and/or some
components can share a housing with a component outside the matching
[0032] As is known in the art, the plasma within a plasma chamber 19
typically undergoes certain fluctuations outside of operational control
so that the impedance presented by the plasma chamber 19 is a variable
impedance. Since the variable impedance of the plasma chamber 19 cannot
be fully controlled, and an impedance matching network may be used to
create an impedance match between the plasma chamber 19 and the RF source
15. Moreover, the impedance of the RF source 15 may be fixed at a set
value by the design of the particular RF source 15. Although the fixed
impedance of an RF source 15 may undergo minor fluctuations during use,
due to, for example, temperature or other environmental variations, the
impedance of the RF source 15 is still considered a fixed impedance for
purposes of impedance matching because the fluctuations do not
significantly vary the fixed impedance from the originally set impedance
value. Other types of RF source 15 may be designed so that the impedance
of the RF source 15 may be set at the time of, or during, use. The
impedance of such types of RF sources 15 is still considered fixed
because it may be controlled by a user (or at least controlled by a
programmable controller) and the set value of the impedance may be known
at any time during operation, thus making the set value effectively a
fixed impedance.
[0033] The RF source 15 may be an RF generator of a type that is
well-known in the art, and generates an RF signal at an appropriate
frequency and power for the process performed within the plasma chamber
19. The RF source 15 may be electrically connected to the RF input 13 of
the RF impedance matching network 11 using a coaxial cable, which for
impedance matching purposes would have the same fixed impedance as the RF
source 15.
[0034] The plasma chamber 19 includes a first electrode 23 and a second
electrode 25, and in processes that are well known in the art, the first
and second electrodes 23, 25, in conjunction with appropriate control
systems (not shown) and the plasma in the plasma chamber, enable one or
both of deposition of materials onto a substrate 27 and etching of
materials from the substrate 27.
[0035] The RF impedance matching network 11 includes a series variable
capacitor 31, a shunt variable capacitor 33, and a series inductor 35
configured as one form an `L` type matching network. In the context of
the present description, the series variable capacitor 31, the shunt
variable capacitor 33, and the series inductor 35 form what is referred
to as the "impedance matching circuit." The shunt variable capacitor 33
is shown shunting to a reference potential, in this case ground 40,
between the series variable capacitor 31 and the series inductor 35, and
one of skill in the art will recognize that the RF impedance matching
network 11 may be configured with the shunt variable capacitor 33
shunting to a reference potential at the RF input 13 or at the RF output
17. Alternatively, the RF impedance matching network 11 may be configured
in other matching network configurations, such as a `T` type
configuration or a `.PI.` type configuration. In certain embodiments, the
variable capacitors and the switching circuit described below may be
included in any configuration appropriate for an RF impedance matching
[0036] Each of the series variable capacitor 31 and the shunt variable
capacitor 33 may be an electronic variable capacitor (EVC), as described
in U.S. Pat. No. 7,251,121, the EVC being effectively formed as a
capacitor array formed by a plurality of discrete capacitors. The series
variable capacitor 31 is coupled in series between the RF input 13 and
the RF output 17 (which is also in parallel between the RF source 15 and
the plasma chamber 19). The shunt variable capacitor 33 is coupled in
parallel between the RF input 13 and ground 40. In other configurations,
the shunt variable capacitor 33 may be coupled in parallel between the RF
output 19 and ground 40. Other configurations may also be implemented
without departing from the functionality of an RF matching network. In
still other configurations, the shunt variable capacitor 33 may be
coupled in parallel between a reference potential and one of the RF input
13 and the RF output 19.
[0037] The series variable capacitor 31 is connected to a series RF choke
and filter circuit 37 and to a series driver circuit 39. Similarly, the
shunt variable capacitor 33 is connected to a shunt RF choke and filter
circuit 41 and to a shunt driver circuit 43. Each of the series and shunt
driver circuits 39, 43 are connected to a control circuit 45, which is
configured with an appropriate processor and/or signal generating
circuitry to provide an input signal for controlling the series and shunt
driver circuits 39, 43. A power supply 47 is connected to each of the RF
input sensor 21, the series driver circuit 39, the shunt driver circuit
43, and the control circuit 45 to provide operational power, at the
designed currents and voltages, to each of these components. The voltage
levels provided by the power supply 47, and thus the voltage levels
employed by each of the RF input sensor 21, the series driver circuit 39,
the shunt driver circuit 43, and the control circuit 45 to perform the
respective designated tasks, is a matter of design choice. In other
embodiments, a variety of electronic components can be used to enable the
control circuit 45 to send instructions to the variable capacitors.
Further, while the driver circuit and RF choke and filter are shown as
separate from the control circuit 45, these components can also be
considered as forming part of the control circuit 45.
[0038] In the exemplified embodiment, the control circuit 45 includes a
processor. The processor may be any type of properly programmed
processing device, such as a computer or microprocessor, configured for
executing computer program instructions (e.g., code). The processor may
be embodied in computer and/or server hardware of any suitable type
(e.g., desktop, laptop, notebook, tablets, cellular phones, etc.) and may
include all the usual ancillary components necessary to form a functional
data processing device including without limitation a bus, software and
data storage such as volatile and non-volatile memory, input/output
devices, graphical user interfaces (GUIs), removable data storage, and
wired and/or wireless communication interface devices including Wi-Fi,
Bluetooth, LAN, etc. The processor of the exemplified embodiment is
configured with specific algorithms to enable matching network to perform
the functions described herein.
[0039] With the combination of the series variable capacitor 31 and the
shunt variable capacitor 33, the combined impedances of the RF impedance
matching network 11 and the plasma chamber 19 may be controlled, using
the control circuit 45, the series driver circuit 39, the shunt driver
circuit 43, to match, or at least to substantially match, the fixed
impedance of the RF source 15.
[0040] The control circuit 45 is the brains of the RF impedance matching
network 11, as it receives multiple inputs, from sources such as the RF
input sensor 21 and the series and shunt variable capacitors 31, 33,
makes the calculations necessary to determine changes to the series and
shunt variable capacitors 31, 33, and delivers commands to the series and
shunt variable capacitors 31, 33 to create the impedance match. The
control circuit 45 is of the type of control circuit that is commonly
used in semiconductor fabrication processes, and therefore known to those
of skill in the art. Any differences in the control circuit 45, as
compared to control circuits of the prior art, arise in programming
differences to account for the speeds at which the RF impedance matching
network 11 is able to perform switching of the variable capacitors 31, 33
and impedance matching.
[0041] Each of the series and shunt RF choke and filter circuits 37, 41
are configured so that DC signals may pass between the series and shunt
driver circuits 39, 43 and the respective series and shunt variable
capacitors 31, 33, while at the same time the RF signal from the RF
source 15 is blocked to prevent the RF signal from leaking into the
outputs of the series and shunt driver circuits 39, 43 and the output of
the control circuit 45. The series and shunt RF choke and filter circuits
37, 41 are of a type known to those of skill in the art.
[0042] The series and shunt variable capacitors 31, 33 may each be an
electronically variable capacitor 51 such as is depicted in FIG. 2A. The
electronically variable capacitor 51 includes a plurality of discrete
capacitors 53 which form an array, and each discrete capacitor 53 has an
electrode on opposite sides thereof, such as is typical of discrete
capacitors that are available on the market.
[0043] Each discrete capacitor 53 has its individual bottom electrode 55
electrically connected to a common bottom electrode 57. The individual
top electrode 59 of each discrete capacitor 53 is electrically connected
to the individual top electrode 59 of adjacent discrete capacitors 53
through an electronic switch 61 that may be activated to electrically
connect the adjacent top electrodes 59. Thus, the individual top
electrodes 59 of each discrete capacitor 53 may be electrically connected
to the top electrodes 59 of one or more adjacent discrete capacitors 53.
The electronic switch 61 is selected and/or designed to be capable of
switching the voltage and current of the RF signal. For example, the
electronic switch 61 may be a PiN/NiP diode, or a circuit based on a
PiN/NiP diode. Alternatively, the electronic switch 61 may be any other
type of appropriate switch, such as a micro electro mechanical (MEM)
switch, a solid-state relay, a field effect transistor, and the like. One
embodiment of the electronic switch 61, in combination with a driver
circuit, is discussed in greater detail below.
[0044] In the configuration of the electronically variable capacitor 51
shown, each individual top electrode 59 may be electrically connected to
between two to four adjacent top electrodes 59, with each connection
being independently regulated by a separate electronic switch 61. The RF
signal input 63 is electrically connected to one of the individual top
electrodes 59, and the RF signal output 65 is electrically connected to
the common bottom electrode 57. Thus, the electronic circuit through
which the RF signal passes may include one, some, or all of the discrete
capacitors 53 by a process of independently activating one or more of the
electronic switches 61 coupled to adjacent ones of the individual top
electrodes 59.
[0045] In other embodiments, the electronically variable capacitor 51 may
be configured to have any layout for the individual top electrodes 59, to
thereby increase or decrease the number of possible electrical
connections between adjacent top electrodes 59. In still other
embodiments, the electronically variable capacitor 51 may have an
integrated dielectric disposed between the bottom electrode 57 and a
plurality of top electrodes 59.
[0046] The electronic switch 61 that is used to connect pairs of adjacent
top electrodes 59 may be a PiN/NiP diode-based switch, although other
types of electronic switches may be used, such as a Micro Electro
Mechanical (MEM) switch, a solid-state relay, a field effect transistor,
and the like. Each electronic switch 61 is switched by appropriate driver
circuitry. For example, each of the series and 651 shunt driver circuits
39, 43 of FIG. 1 may include several discrete driving circuits, with each
discrete driving circuit configured to switch one of the electronic
switches 61 between an on state and an off state. By controlling the on
and off states of each discrete capacitor 53 within the electronically
variable capacitor 51, the capacitance of the electronically variable
capacitor 51 may be controlled and varied. Each unique configuration of
the on and off states of the plurality of discrete capacitors 53 is
referred to herein as an "array configuration" of the variable capacitor
51, and each array configuration is associated with a capacitance of the
electronically variable capacitor 51. In certain embodiments, each array
configuration results in a unique capacitance for the electronically
variable capacitor 51, so that there is a direct correlation between each
array configuration and the capacitance value of the electronically
variable capacitor 51.
[0047] FIG. 2B shows an electronic circuit 650 for providing a variable
capacitance according to one embodiment. The circuit 650 utilizes an EVC
651 that includes two capacitor arrays 651a, 651b. The first capacitor
array 651a has a first plurality of discrete capacitors, each having a
first capacitance value. The second capacitor array 651b has a second
plurality of discrete capacitors, each having a second capacitance value.
The first capacitance value is different from the second capacitance
value such that the EVC 651 can provide coarse and fine control of the
capacitance produced by the EVC 651. The first capacitor array and the
second capacitor array are coupled in parallel between a signal input 613
and a signal output 630. The capacitor arrays 651a, 651b and their
discrete capacitors may be arranged in manner similar to that shown in
FIG. 2A, or in an alternative manner.
[0048] The first and second capacitance values can be any values
sufficient to provide the desired overall capacitance values for the EVC
651. In one embodiment, the second capacitance value is less than or
equal to one-half (1/2) of the first capacitance value. In another
embodiment, the second capacitance value is less than or equal to
one-third (1/3) of the first capacitance value. In yet another
one-fourth (1/4) of the first capacitance value.
[0049] The electronic circuit 650 further includes a control circuit 645.
The control circuit 645 is operably coupled to the first capacitor array
651a and to the second capacitor array 651b by a command input 629, the
command input 629 being operably coupled to the first capacitor array
651aand to the second capacitor array 651b. In the exemplified
embodiment, the command input 629 has a direct electrical connection to
the capacitor arrays 651a, 651b, though in other embodiments this
connection can be indirect. The coupling of the control circuit 645 to
the capacitor arrays 651a, 651b will be discussed in further detail
[0050] The control circuit 645 is configured to alter the variable
capacitance of the EVC 651 by controlling on and off states of (a) each
discrete capacitor of the first plurality of discrete capacitors and (b)
each discrete capacitor of the second plurality of discrete capacitors.
The control circuit 645 can have features similar to those described with
respect to control circuit 45 of FIG. 1. For example, the control circuit
645 can receive inputs from the capacitor arrays 651a, 651b, make
calculations to determine changes to capacitor arrays 651a, 651b, and
delivers commands to the capacitor arrays 651a, 651b for altering the
capacitance of the EVC 651.
[0051] Similar to EVC 51 discussed with respect to FIG. 2A, the EVC 651 of
FIGS. 2B and 2C can include a plurality of electronic switches. Each
electronic switch can be configured to activate and deactivate one or
more discrete capacitors.
[0052] As with the control circuit 45 of FIG. 1, the control circuit 645
can also be connected to a driver circuit 639 and an RF choke and filter
circuit 637. The control circuit 645, driver circuit 639, and RF choke
and filter circuit 637 can have capabilities similar to those discussed
with regard to FIG. 1. In the exemplified embodiment, the driver circuit
639 is operatively coupled between the control circuit 645 and the first
and second capacitor arrays 651a, 651b. The driver circuit 639 is
configured to alter the variable capacitance based upon a control signal
received from the control circuit 645. The RF filter 637 is operatively
coupled between the driver circuit 639 and the first and second capacitor
arrays 651a, 651b. In response to the control signal sent by the control
unit 645, the driver circuit 639 and RF filter 637 are configured to send
a command signal to the command input 629. The command signal is
configured to alter the variable capacitance by instructing at least one
of the electronic switches to activate or deactivate (a) at least one the
discrete capacitors of the first plurality of discrete capacitors or (b)
at least one of the discrete capacitors of the second plurality of
[0053] In the exemplified embodiment, the driver circuit 639 is configured
to switch a high voltage source on or off in less than 15 .mu.sec, the
high voltage source controlling the electronic switches of each of the
first and second capacitor arrays for purposes of altering the variable
capacitance. The EVC 651, however, can be switched by any of the means or
speeds discussed in the present application.
[0054] The control circuit 645 can be configured to calculate coarse and
fine capacitance values to be provided by the respective capacitor arrays
651a, 651b. In the exemplified embodiment, the control circuit 645 is
configured to calculate a coarse capacitance value to be provided by
controlling the on and off states of the first capacitor array 651a.
Further, the control circuit is configured to calculate a fine
capacitance value to be provided by controlling the on and off states of
the second capacitor array 651b. In other embodiments, the capacitor
arrays 651a, 651b can provide alternative levels of capacitance.
[0055] In other embodiments, the EVC can utilize additional capacitor
arrays. FIG. 2C shows an embodiment of an EVC 651' in which a third
capacitor array 651c' is utilized to provide an additional degree of
control over the variable capacitance. Like the EVC 651 of FIG. 2B, the
EVC 651' of FIG. 2C includes an input 613', an output 630', and a command
input 629'. Similar to the first and second capacitor arrays 651a',
651b', the third capacitor array 651c' can have a third plurality of
discrete capacitors. Each discrete capacitor of the third plurality of
discrete capacitors can have a third capacitance value, this value being
different from both the first capacitance value and the second
capacitance value. The first capacitor array 651a', second capacitor
array 651b', and third capacitor array 651c' can be coupled in parallel
between the signal input 613' and the signal output 630'. A control
circuit can be operably coupled to the third capacitor array 651c', and
be further configured to alter the variable capacitance by controlling on
and off states of each discrete capacitor of the third plurality of
discrete capacitors. Additional capacitor arrays enable an EVC to utilize
several different capacitance values in controlling the overall EVC
capacitance. In other embodiments, the third plurality of discrete
capacitors can be replaced with a single discrete capacitor, or an
alternative device for varying the overall capacitance of the EVC 651'.
[0056] The first, second, and third capacitance values of EVC 651' can be
any values sufficient to provide the desired overall capacitance values
for EVC 651'. In one embodiment, the second capacitance value is less
than or equal to one-half (1/2) of the first capacitance value, and the
third capacitance value is less than or equal to one-half (1/2) of the
second capacitance value. In another embodiment, the second capacitance
value is less than or equal to one-third (1/3) of the first capacitance
value, and the third capacitance value is less than or equal to one-third
(1/3) of the second capacitance value.
[0057] The EVCs 651, 651' of FIGS. 2B and 2C, respectively, can be used in
most systems requiring a varying capacitance. For example, the EVCs 651,
651' can be used as a series EVC and/or a shunt EVC in a matching
network, such as the RF matching network 11 discussed above with respect
to FIG. 1. It is often desired that the differences between the
capacitance values allow for both a sufficiently fine resolution of the
overall capacitance of the circuit and a wide range of capacitance values
to enable a better impedance match at the input of a RF matching network,
and EVCs 651, 651' allow this.
[0058] The EVCs 651, 651' can also be used in a system or method for
fabricating a semiconductor, a method for controlling a variable
capacitance, and/or a method of controlling an RF impedance matching
network. Such methods can include altering at least one of the series
variable capacitance and the shunt variable capacitance to the determined
series capacitance value and the shunt capacitance value, respectively.
This altering can be accomplishing by controlling, for each of the series
EVC and the shunt EVC, on and off states of each discrete capacitor of
each plurality of discrete capacitors. In other embodiments, the EVC 651,
651' and circuit 650 can be used in other methods and systems to provide
a variable capacitance.
[0059] FIG. 3 shows an embodiment of a high voltage switching circuit 101,
which is shown including a driver circuit 102 and a PiN/NiP diode 103 as
an electronic switch. Although this switching circuit is shown with the
driver circuit 102 integrated with the PiN/NiP diode 103, one of skill in
the art will understand that in practice, the PiN/NiP diode 103, or any
other type of electronic switch, may be integrated with the discrete
capacitors in an EVC that is part of an RF impedance matching network,
with the RF choke and filter circuit connected between the output of the
driver circuit 102 and the PiN/NiP diode 103.
[0060] The switching circuit 101 may be used for switching one of the
discrete capacitors in an EVC between an `ON` state and an `OFF` state.
One of skill in the art will recognize that the use of the PiN/NiP diode
103 in this embodiment is exemplary, and that the switching circuit 101
may include other types of circuitry that does not include the PiN/NiP
diode 103, yet still provides some of the same fast switching advantages
of the PiN/NiP diode 103 for switching one of the discrete capacitors in
an EVC. One of skill in the art will also recognize that certain
components of the driver circuit 102 may be replaced with other
components that perform the same essential function while also greater
allowing variability in other circuit parameters (e.g., voltage range,
current range, and the like).
[0061] This driver circuit 102 has an input 105 which receives a common
input signal for controlling the voltage on the common output 107 that is
connected to and drives the PiN/NiP diode 103. The voltage on the common
output 107 switches the PiN/NiP diode 103 between the `ON` state and the
`OFF` state, thus also switching `ON` and `OFF` the discrete capacitor to
which the PiN/NiP diode 103 is connected. The state of the discrete
capacitor, in this exemplary embodiment, follows the state of the state
of the PiN/NiP diode 103, such that when the PiN/NiP diode 103 is `ON`,
the discrete capacitor is also `ON`, and likewise, when the PiN/NiP diode
103 is `OFF`, the discrete capacitor is also `OFF`. Thus, statements
herein about the state of the PiN/NiP diode 103 inherently describe the
concomitant state of the connected discrete capacitor of the EVC.
[0062] The input 105 is connected to both a first power switch 111 and
into a second power switch 113. As depicted, the first power switch 111
is an optocoupler phototransistor 111', and the second power switch 113
is a MOSFET 113'. A high voltage power supply 115 is connected to the
first power switch 111, providing a high voltage input which is to be
switchably connected to the common output 107. A low voltage power supply
117 is connected to the second power switch 113, providing a low voltage
input which is also to be switchably connected to the common output 107.
In the configuration of the driver circuit 102 shown, the low voltage
power supply 117 may supply a low voltage input which is about -5 V. Such
a low voltage, with a negative polarity, is sufficient to provide a
forward bias for switching the PiN/NiP diode 103. For other
configurations of the driver circuit 102, a higher or lower voltage input
may be used, and the low voltage input may have a positive polarity,
depending upon the configuration and the type of electronic switch being
[0063] The common input signal asynchronously controls the `on` and `off`
states of the first power switch 111 and the second power switch 113,
such that when the first power switch 111 is in the `on` state, the
second power switch 113 is in the `off` state, and similarly, when the
first power switch is in the `off` state, the second power switch 113 is
in the `on` state. In this manner, the common input signal controls the
first power switch 111 and the second power switch 113 to asynchronously
connect the high voltage input and the low voltage input to the common
output for purposes of switching the PiN/NiP diode 103 between the `ON`
state and the `OFF` state.
[0064] The input 105 may be configured to receive any type of appropriate
control signal for the types of switches selected for the first power
switch 111 and the second power switch 113, which may be, for example, a
+5 V control signal. Of course, to maintain simplicity of the overall
driver circuit 102 and avoid incurring additional manufacturing costs,
the first and second power switches 111, 113 are preferably selected so
that they may directly receive the common input signal without requiring
additional circuitry to filter or otherwise transform the common input
[0065] The switching circuit 101 has design features which make it
particularly useful for switching between a high voltage input and a low
voltage input on the common output quickly and without the need to float
the drive circuit, with respect to the high voltage input, or require use
of special gate charging circuits due to isolation of the input signal
from the high voltage input. Another advantage of the switching circuit
101 is that it provides the ability to switch the common output between
voltage modes quickly, within the time frame of about 15 .mu.sec or less.
The simplicity of the switching circuit 101 should considerably reduce
manufacturing costs, especially when compared to other circuits
performing similar functionality, and it should also significantly reduce
space requirements for the circuit, and again, especially as compared to
other circuits performing similar functionality. These advantages make
the switching circuit 101 particularly advantageous with the incorporated
PiN/NiP diode 103.
[0066] One of the ways in which these advances are realized is the first
power switch 111 being a monolithic circuit element, such as the
optocoupler phototransistor 111'. A monolithic element reduces both cost
and space requirements. When an optocoupler phototransistor 111' is used
as the monolithic element, it can perform the necessary high voltage
switching quickly, and it serves to isolate the high voltage input from
the common input signal. Other, as yet unrealized advantages may also be
present through the use of an optocoupler phototransistor 111'.
[0067] An optocoupler phototransistor 111' serves well as the first power
switch 111 for use in conjunction with the PiN/NiP diode 103 because of
the low current requirements for the PiN/NiP diode 103 when in the `OFF`
state. During the `OFF` state, the PiN/NiP diode 103 is reverse biased,
and thus non-conducting, and as such the `OFF` state current requirement
falls within the current handling capability of most optocoupler
phototransistors. In addition, in implementations when one or both of the
voltage requirements or the current requirements exceed the
specifications for a single optocoupler phototransistor, additional
optocoupler phototransistors may be added into the circuit in series or
in parallel to increase the voltage and/or current handling capabilities
of the switching circuit.
[0068] To further highlight the advantages of the switching circuit 101,
its operation is detailed when the first power switch 111 is an
optocoupler phototransistor 111' and the second power switch 113 is an
appropriate MOSFET 113'. In this example, the common input signal may be
a 5 V control signal which is alternated between a first voltage level
and a second voltage level that serve to switch both the optocoupler
phototransistor 111' and the MOSFET 113' between `on` and `off` states.
The manner of implementing a 5 V control signal is well known to those of
[0069] When the PiN/NiP diode 103 is to be turned to the `OFF` state, the
optocoupler phototransistor 111' is turned to the `on` state by applying
the first voltage level from the common input signal across the
photodiode inputs of the optocoupler phototransistor 111'. Turning the
optocoupler phototransistor 111' to the `on` state connects high voltage
input to the common output 107, thereby reverse biasing the PiN/NiP diode
103. At the same time, during this `OFF` state of the PiN/NiP diode 103,
application of the first voltage level from the common input signal to
the MOSFET 113' places the MOSFET 113' in the `off` state, thereby
disconnecting low voltage input from the common output 107.
[0070] When the PiN/NiP diode 103 is to be turned to the `ON` state, the
optocoupler phototransistor 111' is turned to the `off` state by applying
the second voltage level from the common input signal across the
optocoupler phototransistor 111' to the `off` state disconnects high
voltage input from the common output 107. At the same time, application
of the second voltage level from the common input signal to the MOSFET
113' places the MOSFET 113' in the `on` state, thereby connecting the low
voltage input to the common output 107. With the MOSFET 113' in the `on`
state, and the optocoupler phototransistor 111' to the `off` state, only
the low voltage input is connected to the common output 107, so that the
PiN/NiP diode 103 is forward biased and placed in the `ON` state.
[0071] As indicated above, the optocoupler phototransistor 111' provides
the advantage that the common input signal is electrically isolated,
through the internal optical switch (not shown) of the optocoupler
phototransistor 111', from the switched high voltage, thus alleviating
the need to float the drive circuit (such as when a MOSFET is used to
switch the high voltage). Use of the optocoupler phototransistor 111'
provides the additional advantage that the driver circuit 102 can quickly
switch the common output 107 between the high voltage input and the low
voltage input, with the switching occurring within the time frame of
about 15 .mu.sec or less. This fast switching time helps reduce switching
loss, thereby reducing stress on the PiN/NiP diode itself, and introduces
improvements in the semiconductor fabrication process by reducing the
amount of time it takes for the RF impedance matching network to create
an impedance match between the RF source and the plasma chamber.
[0072] The use of optocoupler phototransistors in the driver circuit 102
also provides advantages for switching a high voltage input in the range
of 500 V-1000 V. Higher or lower voltages may also be switched with this
driver circuit 102. The high voltage input may therefore differ from the
low voltage input by at least two or three orders of magnitude, or more.
Advantageously, when the switching circuit 101 incorporates the PiN/NiP
diode 103, the high voltage input and the low voltage input may have
opposite polarities.
[0073] The ability of the driver circuit 102 to provide quick switching
capabilities is exemplified by the graphs 151, 161 of FIGS. 4 and 5. The
voltage curve 153 of FIG. 4 shows the voltage on the common output 107 of
the driver circuit 102 in order to switch the connected PiN/NiP diode 103
to the `OFF` state. As is shown by the voltage curve 153, the driver
circuit 102 is capable of switching to connect the high voltage input,
which in this example is approximately 1,000 V, to the common output 107
within about 11 .mu.sec. The voltage curve 163 of FIG. 5 shows the
voltage on the common output 107 of the driver circuit 102 in order to
switch the connected PiN/NiP diode 103 to the `ON` state. As is shown by
the voltage curve 163, the driver circuit 102 is capable of switching to
connect the low voltage input, which in this example is approximately -12
V, to the common output 107 within about 9 .mu.sec. Thus, an RF impedance
matching network which includes EVCs and switching circuits, as described
above, shows significant improvements as compared to an RF impedance
matching network which includes VVCs.
[0074] A switching circuit 201 which includes a driver circuit 202 having
multiple optocoupler phototransistors 203 to increase the high voltage
capabilities is shown in FIG. 6A. Like the driver circuit 102 of FIG. 3,
this driver circuit 202 includes an input 205 which receives a common
input signal for controlling the voltage on the common output 207. The
switching circuit 201 includes a PiN/NiP diode 209 connected to the
common output 207, and the voltage on the common output 207 may be used
to switch the PiN/NiP diode 209 between `ON` state and `OFF` states. The
input 205 is connected to both a first power switch 211, which includes
the optocoupler phototransistors 203, and to a second power switch 213,
which includes another optocoupler phototransistor 215 and a MOSFET 217.
[0075] A high voltage power supply 219 is connected to the first power
switch 211, providing a high voltage input which is to be switchably
connected to the common output 207. A low voltage power supply 221 is
connected to the second power switch 213, providing a low voltage input
which is also to be switchably connected to the common output 207.
[0076] The optocoupler phototransistors 203 of the first power switch 211
are connected in series to each other in order to enable the first power
switch 211 to switch higher voltages onto the common output 207 in the
same manner as discussed above with a single optocoupler phototransistor.
With appropriate selection of the optocoupler phototransistors 203, the
first power switch 211, as shown, is capable of switching about 1000 V or
more from the high voltage power supply 219 to the common output 207.
Additional optocoupler phototransistors may be added in series for the
first power switch 211 to increase the high voltage switching
capabilities. One of skill in the art will recognize that one or more
optocoupler phototransistors may be connected in parallel to each other
to increase the current load capabilities of the first power switch 211.
One optocoupler phototransistor may be used to switch low voltages
through the design rating of the optocoupler phototransistor, with more
optocoupler phototransistors being added to switch higher voltages.
[0077] The optocoupler phototransistor 215 of the second power switch 213
receives the common input signal, like the optocoupler phototransistors
203 of the first power switch 211. This optocoupler phototransistor 215
is connected to the MOSFET 217 and places the MOSFET 217 in the `off`
state by connecting the source to the gate when the common input signal
places the first power switch 211 in the `on` state. In this
configuration, when the MOSFET 217 is in the `on` state, the second power
switch 213 is also in the `on` state, connecting the low power input to
the common output 207 Likewise, when the MOSFET 217 is in the `off`
state, the second power switch 213 is also in the `off` state, so that
the low power input is disconnected from the common output 207. When the
first power switch is in the `off` state, optocoupler phototransistor 215
disconnects the gate from the source, so that the MOSFET 217 placed in
the `on` state by the gate being connected to the voltage V2, which is an
appropriate voltage for controlling the gate of the MOSFET 217.
[0078] FIG. 6B shows a switching circuit 201-1 according to yet another
embodiment of the invention. In this embodiment, the switching circuit
201-1 can utilize a cascode structure 218-1 to increase high voltage
capabilities and increase switching speed while providing a simple
control scheme.
[0079] In the exemplified embodiment, the switching circuit 201-1 includes
a driver circuit 202-1 (sometimes referred to as a control circuit) and a
PiN/NiP diode 209-1. As in other embodiments, the driver circuit 202-1
includes an input 205-1 that receives a common input signal for
controlling the voltage on the common output 207-1. The PiN/NiP diode
209-1 is connected to the common output 207-1, and the voltage on the
common output 207-1 may be used to switch the PiN/NiP diode 209-1 between
`ON` and `OFF` states. The common input 205-1 is connected to both a
first power switch 211-1 and a second power switch 213-1.
[0080] As with switching circuits 101 and 201, switching circuit 201-1 may
be used for switching one of the discrete capacitors in an EVC between an
`ON` state and an `OFF` state. One of skill in the art will recognize
that the use of the PiN/NiP diode 209-1 in this embodiment is exemplary,
and that the switching circuit 201-1 may include other types of circuitry
that does not include the PiN/NiP diode 209-1, yet still provides some of
the same advantages of the PiN/NiP diode 209-1 for switching one of the
discrete capacitors in an EVC. One of skill in the art will also
recognize that certain components of the driver circuit 202-1 may be
replaced with other components that perform the same essential function
while also greater allowing variability in other circuit parameters
(e.g., voltage range, current range, and the like). One of skill in the
art will also recognize that certain commonly known components have been
omitted from discussion for clarity.
[0081] The PiN/NiP diode 209-1 is configured to receive an RF signal. In
the exemplified embodiment, the RF signal is a high voltage RF signal
(e.g., 1000 V peak amplitude, 3000 V peak amplitude, or 4000 V peak
amplitude). Accordingly, a high voltage power supply (e.g., 1200 VDC for
a 1000V peak amplitude RF signal) is required to reverse bias the PiN/NiP
diode 209-1 and thereby turn the switching circuit 201-1 `OFF`. The high
voltage of the high voltage power supply 219-1 can be two orders of
magnitude or more greater than the low voltage of the low voltage power
supply 221-1.
[0082] The high voltage power supply 219-1 is connected to the first power
switch 211-1, providing a high voltage input which is to be switchably
connected to the common output 207-1. A low voltage power supply 221-1 is
connected to the second power switch 213-1, providing a low voltage input
which is also to be switchably connected to the common output 207-1. In
the configuration of the driver circuit 202-1 shown, the low voltage
power supply 221-1 may supply a low voltage input which is about -5 V.
Such a low voltage, with a negative polarity, is sufficient to provide a
forward bias for switching the PiN/NiP diode 209-1. For other
configurations of the driver circuit 202-1, a higher or lower voltage
input may be used, and the low voltage input may have a positive
polarity, depending upon the configuration and the type of electronic
switch being controlled.
[0083] The common input signal asynchronously controls the `on` and `off`
states of the first power switch 211-1 and the second power switch 213-1,
such that when the first power switch 211-1 is in the `on` state, the
second power switch 213-1 is in the `off state, and similarly, when the
first power switch 211-1 is in the `off` state, the second power switch
213-1 is in the `on` state. In this manner, the common input signal
controls the first power switch 211-1 and the second power switch 213-1
to asynchronously connect the high voltage input and the low voltage
input to the common output for purposes of switching the PiN/NiP diode
209-1 between the `ON` state and the `OFF` state.
[0084] The common input 205-1 may be configured to receive any type of
appropriate control signal for the types of switches selected for the
first power switch 211-1 and the second power switch 213-1, which may be,
for example, a +5 V control signal.
[0085] The switching circuit 201-1 has design features which make it
201-1 is that it can provide the ability to switch the common output
between voltage modes quickly, within the time frame of about 5 .mu.sec
or less. The simplicity of the switching circuit 201-1 should
considerably reduce manufacturing costs, especially when compared to
other circuits performing similar functionality, and it should also
significantly reduce space requirements for the circuit, and again,
especially as compared to other circuits performing similar
functionality. These advantages make the switching circuit 201-1
particularly advantageous with the incorporated PiN/NiP diode 209-1.
[0086] Similar to first power switches 111 and 211, first power switch
211-1 can utilize at least one optocoupler phototransistor 203-1. (The
terms optocoupler and optocoupler phototransistor are used
interchangeably herein.) In the exemplified embodiment, three optocoupler
phototransistors 203-1 are utilized. The high voltage power supply 219-1
is connected to the collector port of the topmost optocoupler
phototransistor 203-1. Advantages of the use of optocoupler
phototransistors in the first power switch are discussed above. The
optocoupler phototransistors 203-1 of the first power switch 211-1 are
connected in series to each other to enable the first power switch 211-1
to switch higher voltages onto the common output 207 in a manner similar
to that discussed above. With appropriate selection of the optocoupler
phototransistors 203-1, the first power switch 211-1 is capable of
switching 1000 V or more from the high voltage power supply 219-1 to the
common output 207-1. In other embodiments, additional optocoupler
phototransistors may be added in series for the first power switch 211-1
to increase the high voltage switching capabilities. In yet other
embodiments, fewer optocoupler phototransistors may be used, including
use of a single optocoupler phototransistor.
[0087] The second power switch 213-1 can include a cascode structure 218-1
designed to increase the blocking voltage capability of the switching
circuit 201-1. The cascode structure 218-1 includes multiple JFETs J1,
J2, J3 in series. These JFETs are connected in series with a low-voltage
MOSFET M2. As a non-limiting example, the JFETs can be 1700 VDC JFETs,
while and the MOSFET can be a 30V MOSFET. Specifically, the MOSFET M2 is
connected in series between the JFETs J1, J2, J3 the and low voltage
power supply. Between each of the JFET gates is a diode D5, D6. In other
embodiments, a single JFET (rather than multiple JFETs) can be utilized
for the cascode structure. A voltage source V2 is connected to the gate
of MOSFET M2. The voltage source V2 is also connected to optocoupler
phototransistor 215-1 (sometimes referred to as input optocoupler 215-1).
When the optocoupler phototransistor 215-1 is turned on, the optocoupler
phototransistor 215-1 can essentially short the gate of MOSFET M2 to the
source of MOSFET M2, turning MOSFET M2 `off`. It is noted that the JFETs,
MOSFETs, and optocoupler phototransistors can be replaced with other
appropriate transistors or switches. Accordingly, a JFET such as one of
JFETs J1, J2, J3 can be referred to as a first transistor, and a MOSFET
such as MOSFET M2 can be referred to as a second transistor.
[0088] When the PiN/NiP diode 209-1 is in the `ON` state, the first power
switch 211-1 is in the `off` state and the second power switch 213-1 is
in the `on` state. In the exemplified embodiment, the PiN/NiP diode 209-1
is put in the `ON` state by applying a first common input signal of +0 V
at the common input 205-1. When the +0 V first common input signal is
applied, input MOSFET M3 (which can be another type of transistor, such
as a BJT, and is sometimes referred to as the input transistor) is turned
`off`. Consequently, no current flows through the photodiode inputs of
the optocoupler phototransistors 203-1, 215-1. Thus, the optocoupler
transistors 203-1, 215-1 are turned `off`, common output 207-1 does not
receive high voltage from the high voltage power supply 219-1, and the
diode 209-1 is not reverse biased.
[0089] At the same time, since optocoupler 215-1 is `off`, the gate of
MOSFET M2 can receive a voltage from voltage V2. R1 and R2 form a voltage
divider for voltage V2, so that the gate of MOSFET M2 receives a divided
voltage from V2. In the exemplified embodiment, voltage V2 is +5 V. The
receipt of divided voltage V2 at the gate of MOSFET M2 causes MOSFET M2
to switch `on`, which turns `on` the first JFET J1 since the gate of
first JFET J1 is then connected to its source. Next, the second JFET J2
can start conducting and turn `on`, since the voltage on the gate of JFET
J5 is -V.sub.F (the forward voltage drop of diode D6). The same process
can be repeated for turning `on` the remaining JFETs (third JFET J3),
until the voltage of the low voltage power supply 221-1 appears at the
common output 207-1, thereby providing the necessary biasing voltage to
forward bias PiN/NiP diode 209-1.
[0090] With the MOSFET M2 in the `on` state, and the optocoupler
phototransistors 203-1, 215-1 in the `off` state, only the low voltage
input is connected to the common output 209-1, so that the PiN/NiP diode
209-1 is forward biased and placed in the `ON` state. When the
optocouplers 203-1 of the first power switch are switched off, a voltage
drop from the high voltage (of high voltage power supply 219-1) to the
low voltage (of the low voltage power supply 221-1) occurs across the
plurality of optocouplers.
[0091] By contrast, when the PiN/NiP diode 209-1 is in the `OFF` state,
the first power switch 211-1 is in the `on` state and the second power
switch 213-1 is in the `off` state. In the exemplified embodiment, the
PiN/NiP diode 209-1 is put in the `ON` state by applying a second common
input signal of +5 V at the common input 205-1. When the +5 V first
common input signal is applied, input MOSFET M3 is turned `on`.
Consequently, current flows through the photodiode inputs of the
optocoupler phototransistors 203-1, 215-1. Thus, the optocoupler
transistors 203-1, 215-1 are turned `on`, and common output 207-1
receives high voltage from the high voltage power supply 219-1 to reverse
bias diode 209-1.
[0092] At the same time, the gate of MOSFET M2 does not receive voltage
V2, because optocoupler 215-1 is `on`, and therefore diverts voltage from
the gate of MOSFET M2. Since the gate of MOSFET M2 does not receive
voltage V2, MOSFET M2 switches `off`, which causes JFETS J1, J2, J3 to
turn off, thereby preventing the low voltage of the low voltage power
supply 221-1 to appear at the common output 207-1.
[0093] In this state, where the first power switch 211-1 is switched `on`
and the second power switch 213-1 is switched `off`, the high voltage
power source can cause a large voltage across the MOSFET M2 and the JFETs
J1, J2, J3. One benefit of this structure is that the MOSFET M2 can be a
low-voltage MOSFET (e.g., 30 V), while the JFETs J1, J2, J3 can be
higher-voltage JFETS (e.g., 1700 V) for handling the high voltage from
the high voltage power source. For different applications, the MOSFET M2
can remain the same (in number and type), while the number or type of
JFETs can be adjusted to handle the voltage requirements. Building a
higher voltage switch can be achieved by simply adding one or more JFETs
in series with the existing JFETs. There is no need to alter the switch
configuration or how the switch needs to be driven. In this manner, the
cascode structure increases the blocking voltage capability of the
switching circuit.
[0094] With MOSFET M2 in the `off` state, and the optocoupler
phototransistors 203-1, 215-1 in the `on` state, only the high voltage
209-1 is reverse biased and placed in the `ON` state.
[0095] The non-linear capacitance range of a single EVC switched by a
switching circuit is shown in the graph 301 of FIG. 7. The single EVC
used to generate the capacitance curve 303 has 24 discrete capacitors in
the manner described above, with the top electrodes of the discrete
capacitors being selectively connected to arrive at the capacitance curve
303 shown. As can be seen, the single EVC may provide a capacitance
ranging from only one active discrete capacitor (i.e., none of the top
electrodes of any of the discrete capacitors are connected, so that the
RF signal only flows through a single discrete capacitor) to all 24
discrete capacitors being active (i.e., all the top electrodes of all the
discrete capacitors are connected). Any number of the 24 discrete
capacitors may be connected, so that the capacitance of the single EVC
may range from a low capacitance, with one active discrete capacitor as
part of the array configuration, to a high capacitance, with all 24
discrete capacitors active as part of the array configuration. The low
capacitance and the high capacitance are a matter of design choice for
the EVC. In the capacitance curve shown, the low capacitance is about 25
pF, while the high capacitance is over 1,600 pF. The number of discrete
capacitance values that is achievable between the low capacitance and the
high capacitance is also a matter of design choice for the EVC, as more
or fewer discrete capacitors may be included as part of the EVC. The only
significant constraints on an EVC are the mechanical limitations posed by
specific implementations (e.g., size or weight restrictions on the EVC).
Mechanical limitations aside, an EVC does not appear to have any issues
for achieving high value capacitance (e.g., 200,000 pF or higher).
[0096] The stable delivered power of an RF impedance matching network
incorporating EVCs is shown in the graph 331 of FIG. 8, which does not
show or take into account switching capabilities of an EVC controlled by
a switching circuit. There are three curves shown in this graph 331: the
output power 333 of the RF signal output from the RF source, which is
about 500 V; the delivered power 335 to the plasma chamber; and the
reflected power 337 back to the RF source. The output power 333 is a
little over 500 V, while the reflected power 337 is in the range of about
10 V, so that the delivered power 335 to the plasma chamber is about 500
V. Not only is the delivered power 335 about 98% of the output power 333,
but the delivered power 335, as can be seen, is substantially stable,
without significant fluctuations. Both the percentage of delivered power
335 and the stability of the delivered power 335 represent significant
improvements over an RF impedance matching network that is based on VVCs.
[0097] When the switching capabilities of an EVC controlled by a switching
circuit, in the manner described above, are incorporated into an RF
impedance matching network, high speed switching is enabled for the RF
impedance matching network. FIG. 9 is a graph 401 having voltage along
the two y-axes and time along the x-axis to show the speed at which an RF
impedance matching network using EVCs performs impedance matching (also
referred to as the "match tune process"). A representation of an RF power
profile 403 is shown, taken at the RF input of an RF impedance matching
network, and the y-axis for the RF power profile has 50 mV divisions. A
representation of the voltage of the common input signal 405 for driver
circuits is also shown in the lower portion of the graph 401, the common
input signal 405 originating from the control circuit of the RF impedance
matching network, and the y-axis for the common input signal 405 has 5 V
divisions. The x-axis has 50 .mu.sec divisions, with the 56 .mu.sec point
marked in approximately the middle of the graph and the t=0 point as
[0098] Initially, a significant amount of reflected power 407 is shown in
the left portion of the RF power profile 403 (i.e., before the 56 .mu.sec
mark). This reflected power represents inefficiencies in the RF power
being transferred between the RF source and the plasma chamber as a
result of an impedance mismatch. At about t=-36 .mu.sec, the match tune
process begins. The first approximately 50 .mu.sec of the match tune
process is consumed by measurements and calculations performed by the
control circuit in order to determine new values for the variable
capacitances of one or both of the series and shunt EVCs.
[0099] FIG. 10 is a flow chart showing a process 500 for matching an
impedance according to one embodiment. Similar to the matching networks
discussed above, the matching network 11 of the exemplified process
includes the following (shown in FIG. 1): an RF input 13 configured to
operably couple to an RF source 15, the RF source 15 having a fixed RF
source impedance (e.g., 50 Ohms); an RF output 17 configured to operably
couple to a plasma chamber 19, the plasma chamber 19 having a variable
plasma impedance; a series electronically variable capacitor ("series
EVC") 31 having a series array configuration, the series EVC 31
electrically coupled in series between the RF input 13 and the RF output
17; a shunt electronically variable capacitor ("shunt EVC") 33 having a
shunt array configuration, the shunt EVC 33 electrically coupled in
parallel between a ground 40 and one of the RF input 13 and the RF output
17; an RF input sensor 21 operably coupled to the RF input 13, the RF
input sensor 21 configured to detect an RF input parameter at the RF
input 13; an RF output sensor 49 operably coupled to the RF output 17,
the RF output sensor 49 configured to detect an RF output parameter; and
a control circuit 45 operatively coupled to the series EVC 31 and to the
shunt EVC 33 to control the series array configuration and the shunt
array configuration. The steps of the exemplified process 500 can be
carried out as part of the manufacture of a semiconductor, where a
substrate 27 is placed in a plasma chamber 19 configured to deposit a
material layer onto the substrate 27 or etch a material layer from the
substrate 27, and plasma is energized within the plasma chamber 19 by
coupling RF power from the RF source 15 into the plasma chamber 19 to
perform a deposition or etching.
[0100] In the exemplified process 500 of FIG. 10, the control circuit 45
is configured and/or programmed to carry out each of the steps. As one of
two initial steps, RF parameters are measured at the RF input 13 by the
RF input sensor 21, and the input impedance at the RF input 13 is
calculated (step 501) using the measured RF parameters. For this
exemplified process 500, the forward voltage and the forward current are
measured at the RF input 13. In certain other embodiments, the RF
parameters may be measured at the RF output 17 by the RF output sensor
49, although in such embodiments, different calculations may be required
than those described below. In still other embodiments, RF parameters may
be measured at both the RF input 13 and the RF output 17.
[0101] The impedance matching circuit, coupled between the RF source 15
and the plasma chamber 19, may be characterized by one of several types
of parameter matrices known to those of skill in the art. An S-parameter
matrix and a Z-parameter matrix are two examples of such parameter
matrices. Other examples include, but are not limited to, a Y-parameter
matrix, a G-parameter matrix, an H-parameter matrix, a T-parameter
matrix, and an ABCD-parameter matrix. Those of skill in the art will
recognize also that these various parameter matrices may be
mathematically converted from one to the other for an electrical circuit
such as a matching network. The second initial step of the exemplified
process 500 is to look up (step 502) the parameter matrix for the
existing configuration of the impedance matching circuit in a parameter
look-up table. The existing configuration of the impedance matching
circuit is defined by existing operational parameters of the impedance
matching circuit, particularly the existing array configurations for both
of the series EVC 31 and the shunt EVC 33. In order to achieve an
impedance match, the existing configuration of the impedance matching
circuit is altered to a new configuration of the impedance matching
circuit as part of the exemplified process 500.
[0102] The parameter look-up table includes a plurality of parameter
matrices, with each parameter matrix being associated with a particular
configuration of the series EVC 31 and the shunt EVC 33. The parameter
look-up table may include one or more of the aforementioned types of
parameter matrices. In the exemplified process 500, the parameter look-up
table includes at least a plurality of S-parameter matrices. In certain
embodiments, the parameter look-up table may include at least a plurality
of Z-parameter matrices. In embodiments in which the parameter look-up
table includes multiple types of parameter matrices, the different types
of parameter matrices are associated within the parameter look-up table
in such a way so as to eliminate the need for mathematical conversions
between the different types of parameter matrices. For example, the
T-parameter matrix may be included as part of the parameter look-up
table, with each T-parameter matrix associated with the associated
S-parameter matrix that would result from conversion between the two
[0103] The input impedance calculation (step 501) and the parameter matrix
look up (step 502) may be performed in any order. With the input
impedance calculated (step 501) and the parameter matrix for the existing
configuration of the impedance matching circuit identified within the
parameter look-up table (step 502) done, the plasma or load impedance may
then be calculated (step 503) using the calculated input impedance and
the parameter matrix for the existing configuration. Next, from the
calculated plasma impedance, the match configurations for the series EVC
31 and the shunt EVC 33 that would achieve an impedance match, or at
least a substantial impedance match, between the RF source 15 and the
plasma chamber 19 are looked up (step 504) in an array configuration
look-up table. These match configurations from the array configuration
look-up table are the array configurations which will result in new
capacitance values for the series EVC 31 and shunt EVC 33, with an
impedance match being achieved with the new array configurations and
associated new capacitance values. The array configuration look-up table
is a table of array configurations for the series EVC 31 and the shunt
EVC 33, and it includes each possible array configuration of the series
EVC 31 and the shunt EVC 33 when used in combination. As an alternative
to using an array configuration look-up table, the actual capacitance
values for the EVCs 31, 33 may be calculated during the process--however,
such real-time calculations of the capacitance values are inherently
slower than looking up the match configurations in the array
configuration look-up table. After the match configurations for the
series EVC 31 and the shunt EVC 33 are identified in the array
configuration look-up table, then one or both of the series array
configuration and the shunt array configuration are altered (step 505) to
the respective identified match configurations for the series EVC 31 and
the shunt EVC 33.
[0104] The altering (step 505) of the series array configuration and the
shunt array configuration may include the control circuit 45 sending a
control signal to the series driver circuit 39 and the shunt driver
circuit 43 to control the series array configuration and the shunt array
configuration, respectively, where the series driver circuit 39 is
operatively coupled to the series EVC 31, and the shunt driver circuit 43
is operatively coupled to the shunt EVC 43. When the EVCs 31, 33 are
switched to the match configurations, the input impedance may match the
fixed RF source impedance (e.g., 50 Ohms), thus resulting in an impedance
match. If, due to fluctuations in the plasma impedance, a sufficient
impedance match does not result, the process of 500 may be repeated one
or more times to achieve an impedance match, or at least a substantial
impedance match.
[0105] The look-up tables used in the process described above are compiled
in advance of the RF matching network being used in conjunction with the
plasma chamber 19. In creating the look-up tables, the RF matching
network 11 is tested to determine at least one parameter matrix of each
type and the load impedance associated with each array configuration of
the series EVC 31 and the shunt EVC 33 prior to use with a plasma
chamber. The parameter matrices resulting from the testing are compiled
into the parameter look-up table so that at least one parameter matrix of
each type is associated with a respective array configuration of the EVCs
31, 33. Similarly, the load impedances are compiled into the array
configuration look-up table so that each parameter matrix is associated
with a respective array configuration of the EVCs 31, 33. The
pre-compiled look-up tables may take into consideration the fixed RF
source impedance (e.g., 50 Ohms), the power output of the RF source, and
the operational frequency of the RF source, among other factors that are
relevant to the operation of the RF matching network. Each look-up table
may therefore have tens of thousands of entries, or more, to account for
all the possible configurations of the EVCs 31, 33. The number of
possible configurations is primarily determined by how many discrete
capacitors make up each of the EVCs 31, 33. In compiling the look-up
tables, consideration may be given to possible safety limitations, such
as maximum allowed voltages and currents at critical locations inside the
matching network, and this may serve to exclude entries in one or more of
the look-up tables for certain configurations of the EVCs 31, 33.
[0106] As is known in the art, the S-parameter matrix is composed of
components called scatter parameters, or S-parameters for short. An
S-parameter matrix for the impedance matching circuit has four
S-parameters, namely S.sub.11, S.sub.12, S.sub.21, and S.sub.22, each of
which represents a ratio of voltages at the RF input 13 and the RF output
17. All four of the S-parameters for the impedance matching circuit are
determined and/or calculated in advance, so that the full S-parameter
matrix is known. The parameters of the other types of parameter matrices
may be similarly determined and/or calculated in advance and incorporated
into the parameter matrix. For example, a Z-parameter matrix for the
impedance matching circuit has four Z-parameters, namely Z.sub.11,
Z.sub.12, Z.sub.21, and Z.sub.22.
[0107] By compiling the parameter look-up table in this manner, the entire
time cost of certain calculations occurs during the testing phase for the
RF matching network, and not during actual use of the RF matching network
11 with a plasma chamber 19. Moreover, because locating a value in a
look-up table can take less time than calculating that same value in real
time, using the look-up table can aid in reducing the overall time needed
to achieve an impedance match. In a plasma deposition or etching process
which includes potentially hundreds or thousands of impedance matching
adjustments throughout the process, this time savings can help add
directly to cost savings for the overall fabrication process.
[0108] From the beginning of the match tune process, which starts with the
control circuit determining the variable impedance of the plasma chamber
and determining the series and shunt match configurations, to the end of
the match tune process, when the RF power reflected back toward the RF
source decreases, the entire match tune process of the RF impedance
matching network using EVCs has an elapsed time of approximately 110
.mu.sec, or on the order of about 150 .mu.sec or less. This short elapsed
time period for a single iteration of the match tune process represents a
significant increase over a VVC matching network. Moreover, because of
this short elapsed time period for a single iteration of the match tune
process, the RF impedance matching network using EVCs may iteratively
perform the match tune process, repeating the two determining steps and
the generating another control signal for further alterations to the
array configurations of one or both of the electronically variable
capacitors. By iteratively repeating the match tune process, it is
anticipated that a better impedance match may be created within about 2-4
iterations of the match tune process. Moreover, depending upon the time
it takes for each repetition of the match tune process, it is anticipated
that 3-4 iterations may be performed in 500 .mu.sec or less. Given the
1-2 sec match time for a single iteration of a match tune process for RF
impedance matching networks using VVCs, this ability to perform multiple
iterations in a fraction of the time represents a significant advantage
for RF impedance matching networks using EVCs.
[0109] Those of skill in the art will recognize that several factors may
contribute to the sub-millisecond elapsed time of the impedance matching
process for an RF impedance matching network using EVCs. Such factors may
include the power of the RF signal, the configuration and design of the
EVCs, the type of matching network being used, and the type and
configuration of the driver circuit being used. Other factors not listed
may also contribute to the overall elapsed time of the impedance matching
process. Thus, it is expected that the entire match tune process for an
RF impedance matching network having EVCs should take no more than about
500 .mu.sec to complete from the beginning of the process (i.e.,
measuring by the control circuit and calculating adjustments needed to
create the impedance match) to the end of the process (the point in time
when the efficiency of RF power coupled into the plasma chamber is
increased due to an impedance match and a reduction of the reflected
power). Even at a match tune process on the order of 500 .mu.sec, this
process time still represents a significant improvement over RF impedance
matching networks using VVCs.
[0110] Table 1 presents data showing a comparison between operational
parameters of one example of an EVC versus one example of a VVC. As can
be seen, EVCs present several advantages, in addition to enabling fast
switching for an RF impedance matching network:
Typical 1000 pF
Parameter EVC Vacuum Capacitors
Capacitance 20 pF~1400 pF 15 pF~1000 pF
Reliability High Low
Response Time ~500 .mu.sec 1 s~2 s
ESR ~13 mW ~20 mW
Voltage 7 kV 5 kV
Current Handling Capability 216 A rms 80 A rms
Volume 4.5 in.sup.3 75 in.sup.3
[0111] As is seen, in addition to the fast switching capabilities made
possible by the EVC, EVCs also introduce a reliability advantage, a
current handling advantage, and a size advantage. Additional advantages
of the RF impedance matching network using EVCs and/or the switching
circuit itself for the EVCs include: [0112] The disclosed RF impedance
matching network does not include any moving parts, so the likelihood of
a mechanical failure reduced to that of other entirely electrical
circuits which may be used as part of the semiconductor fabrication
process. For example, the typical EVC may be formed from a rugged ceramic
substrate with copper metallization to form the discrete capacitors. The
elimination of moving parts also increases the resistance to breakdown
due to thermal fluctuations during use. [0113] The EVC has a compact size
as compared to a VVC, so that the reduced weight and volume may save
valuable space within a fabrication facility. [0114] The design of the
EVC introduces an increased ability to customize the RF matching network
for specific design needs of a particular application. EVCs may be
configured with custom capacitance ranges, one example of which is a
non-linear capacitance range. Such custom capacitance ranges can provide
better impedance matching for a wider range of processes. As another
example, a custom capacitance range may provide more resolution in
certain areas of impedance matching. A custom capacitance range may also
enable generation of higher ignition voltages for easier plasma strikes.
[0115] The short match tune process (.about.500 .mu.sec or less) allows
the RF impedance matching network to better keep up with plasma changes
within the fabrication process, thereby increasing plasma stability and
resulting in more controlled power to the fabrication process. [0116] The
use of EVCs, which are digitally controlled, non-mechanical devices, in
an RF impedance matching network provides greater opportunity to fine
tune control algorithms through programming. [0117] EVCs exhibit superior
low frequency (kHz) performance as compared to VVCs.
[0118] In systems such as the matching networks and semiconductor
manufacturing systems discussed above, heat can be generated that
compromises system operation. The embodiments discussed below can be
utilized to help cool such systems, as well as other types of systems.
[0119] In one embodiment, the embodiments can enhance the cooling capacity
of a water-cooling heat sink by adding a heat exchanger to the heat sink
and mounting a fan directly over or adjacent to the heat exchanger. By
this design, when electrical components heat the air within an enclosure,
the fan can blow the heated air onto the heat exchanger of the heat sink.
The heat sink can transfer the heat to cool water running through a tube
(e.g., a copper pipe) in the heat sink. The heated water can then be
removed from the heat sink at a water output, thereby removing heat from
the enclosure. Since the heat that is built up is removed by the heat
sink by way of the cool water, the generator enclosure can be totally
sealed to the outside atmosphere. This in turn eliminates the outgassing
concern from damaged components and assemblies and prevents contamination
of the fab.
[0120] FIG. 11 show a system 710 according to one embodiment of the
invention. In the exemplified embodiment, the system 710 includes a
matching network, such as the matching networks discussed above. In other
embodiments, the system can be any system generating heat, including an
RF generator, or a combination RF generator and matching network. In the
exemplified embodiment, the system 710 includes electrical components
717, 718 for a matching network, and the matching networks forms part of
a semiconductor manufacturing system, such as the systems discussed
[0121] The exemplified system 710 includes an enclosure 712 and a cooling
system 720. FIG. 11 shows a side view of the system 710 where a side
panel of the enclosure 712 is removed. Within the enclosure 712 are shelf
electrical components 717 located on a component shelf 714, as well as
other electrical components 718. The exemplified enclosure 712 (when the
front side panel is in place) is sealed so as to prevent air and exhaust
from escaping the enclosure. While no enclosure is completely sealed to
prevent the escape of all air and exhaust, the enclosure is designed to
reasonably prevent most air and exhaust from escaping. This can prevent
outgassing and contamination of the surrounding environment, which is
particularly helpful in a semiconductor fab.
[0122] The cooling system 720 includes a heat sink 730 and a fan 750
enclosed by the enclosure 712 for causing air flow A. In the exemplified
embodiment, the heat sink 730 is within the enclosure 712, though in
other embodiments a portion of the heat sink may be outside the enclosure
712. The fan 750 can direct hot air A from the first electrical
components 718 to the heat exchanger 740 of the heat sink 730. The fan
750 can be mounted on or adjacent to the heat sink. As used herein, the
term "fan" refers to any device for pushing air within the system to be
[0123] Cool water enters the heat sink 730 at the water input 764. The
cool water travels through a tube 762 in the heat sink 730. Heat is
transferred from the heat exchanger 740 to the water flowing through the
heat exchanger 740, and the heated water is removed from the heat sink
730 at the water output 766, thereby removing heat from the enclosure
712. It is noted that, while the exemplified embodiment utilizes water
traveling through the tube, other liquids can be utilized instead of
[0124] FIGS. 12-14 show the heat sink 730 apart from the enclosure 712 and
the other components of the cooling system 720. FIG. 12 is a perspective
bottom view of the heat sink 730. The heat sink 730 includes a main
housing portion 732 and a heat exchanger portion 740.
[0125] The heat exchanger 740 can be affixed directly to the main housing
732 of the heat sink 730. In another embodiment, the heat exchanger can
be created by cutting fins directly into the heat sink 730. Affixed fins
can be, for example, die cast or molded. The heat exchanger 740 can be
made of a material with a high rate of thermal conductivity (e.g.,
aluminum or copper). The geometry of the heat exchanger 740 increases the
surface area of contact between the tube 738 (and the water it carries)
and the heated air. This configuration pulls heat away from the air in
the enclosure 712 at a high rate, cooling the air and, consequently, the
electrical components 718. The geometry of the heat exchanger 740 can any
geometry that effectively increases the surface area of the tube 738. As
used herein, the term "heat exchanger" can refer to any device configured
to transfer heat from one medium to another.
[0126] The main housing 732 can have a main housing surface 733 that can
receive electrical components or rest against a surface that receives
electrical components. The water flow W of the cool water in the tube 762
is shown. The tube 762 can extend into and out of the heat exchanger 740,
the tube 762 configured to transport water through the heat exchanger
740. The tube 762 can also extend into and out of the main housing 732.
In other embodiments, the main housing 732 can be omitted, and the tube
762 can extend through the heat exchanger 740.
[0127] FIG. 13 shows a perspective top view of the heat sink 730. In the
exemplified embodiment, the main housing top surface 734 can be attached
to the component shelf surface 716 (FIG. 11) such that the two surfaces
734, 716 are in contact with each other. The surfaces 734, 716 can
comprise thermally conductive material. In another embodiment, the main
housing surface (top 734 or bottom 733) can be configured to received
electrical components directly on the main housing surface 734, 733.
[0128] FIG. 14 shows bottom view of the heat sink 730. The exemplified
main housing 732 has a first edge 737 and a second edge 738 opposite the
first edge 737. The heat exchanger 740 has a first edge 742 and a second
edge 744 opposite the first edge 742. The main housing second edge 738 is
adjacent the heat exchanger first edge 742. The tube 762 enters the main
housing 732 at the main housing first edge 737. The tube 762 enters the
heat exchanger 740 at the heat exchanger first edge 742. The tube 762
exits the heat exchanger 740 at the heat exchanger first edge 742.
Further, the tube 762 exits the main housing 732 at the main housing
first edge 737. The main housing 32 and the heat exchanger 40 are located
side-by-side and contact each other along edges 28 and 42, respectively.
In the exemplified heat sink, the tube 762 extends along a first side 35
of the main housing 32 and a second side 36 of the main housing 32
opposite the first side 35.
[0129] In other embodiments, other configurations can be utilized. For
example, the main housing could be eliminated, or the tube could enter
that heat exchanger before entering the main housing. Further, rather
than entering along a first side and then exiting along a second,
opposite side, the tube could proceed in any manner, such as zig-zagging
back-and-forth between the two sides.
[0130] In addition to the foregoing, means can be provided inside the
system to detect the fault and generate a fault signal that causes the
removal of power from the system to prevent further damage. For example,
a fault signal could cause the removal of power from the inputs of an RF
generator and an RF matching network to prevent further damage. In one
embodiment, the fault signal can be received by a control circuit, such
as control circuit 45 (FIG. 1), which in turn causes the removal of power
from the inputs. The unit can go to a safe condition and send an alarm to
a host computer in a fab. This can be accomplished with a variety of
sensors that monitor various conditions. For example, the sensors can
include an ambient air temperature sensor and a heat sink temperature.
Other features that can be monitored include a blocked fan, over
dissipation, and/or a power supply failure. By monitoring such features
and triggering a fault, the system can not only prevent the outgassing of
gases from failed components, but can also restrict the amount of
outgassing by terminating the power that feeds into the failure, thus
limiting the damage, preventing more serious failure, and preventing the
failure of other associated circuitry outside the enclosed system. In
addition to or in place of the fault signal that is communicated to the
semiconductor fabrication system, the RF generator or the RF matching
network may open the system interlock, directly resulting in the shutdown
of any power generation source connected to the inputs of the RF
generator or the RF matching network.
[0131] Since the enclosure is completely enclosed, any humidity left in
the enclosure may condense as the chamber is heated and cooled.
Therefore, it may be necessary to either purge the enclosure with a small
flow of clean dry air or Nitrogen (N.sub.2) with a return port for
exhausting this flow so as to maintain the integrity of the enclosure to
the outside atmosphere. Alternatively, ports might be provided to purge
the enclosure with Nitrogen to remove the humidity and then close the
ports after sealing the enclosure.
[0132] FIG. 15 is a flow chart for a method 770 of cooling an enclosure
according to one embodiment. The exemplified method 770 cools an
enclosure that encloses electrical components and is sealed to prevent
air and exhaust from escaping the enclosure, though the invention is not
so limited. The method 770 comprises positioning a heat sink at least
partially within the enclosure (operation 771). Similar to above, the
heat sink comprises a heat exchanger and a tube extending into and out of
the heat exchanger, the tube configured to transport water through the
heat exchanger. The method 770 further comprises, by a fan enclosed by
the enclosure, pushing air heated by electrical components onto the heat
exchanger (operation 772). The method 770 further comprises receiving, at
the heat exchanger, heat from the pushed air (operation 773), and
transferring, by the heat exchanger, the received heat to water being
transported by the tube through the heat exchanger (operation 774).
[0133] In another embodiment, a method of manufacturing a semiconductor is
utilized. The method includes operably coupling a matching network
between an RF source and a plasma chamber, for example, as in FIG. 1
described above. The plasma chamber is configured to deposit a material
electrical components of the matching network are enclosed by an
enclosure (such as enclosure 712 discussed above) that is configured to
prevent air and exhaust from escaping the enclosure. The method also
includes positioning a heat sink (such as heat sink 730 discussed above)
at least partially within the enclosure; placing a substrate in the
heat exchanger, the received heat to water being transported by the tube
[0134] Some of the foregoing embodiments discuss use of cooling system for
an RF system used in semiconductor manufacturing. It is noted, however,
that the invention is not so limited, as the cooling systems and methods
can be used with other systems that require cooling.
[0135] While the invention has been described with respect to specific
examples including presently preferred modes of carrying out the
invention, those skilled in the art will appreciate that there are
numerous variations and permutations of the above described systems and
techniques. It is to be understood that other embodiments may be utilized
and structural and functional modifications may be made without departing
from the scope of the present invention. Thus, the spirit and scope of
the invention should be construed broadly as set forth in the appended
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