Source: https://patents.google.com/patent/US8885757B2/en
Timestamp: 2018-11-21 01:07:06
Document Index: 688556290

Matched Legal Cases: ['Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61', 'Application No. 61']

US8885757B2 - Calibration of MIMO systems with radio distribution networks - Google Patents
Calibration of MIMO systems with radio distribution networks Download PDF
US8885757B2
US8885757B2 US14102539 US201314102539A US8885757B2 US 8885757 B2 US8885757 B2 US 8885757B2 US 14102539 US14102539 US 14102539 US 201314102539 A US201314102539 A US 201314102539A US 8885757 B2 US8885757 B2 US 8885757B2
US14102539
US20140098902A1 (en )
A system and method of maintaining performance of an RF Distribution Network that combines signals (phases and amplitudes) passing through components that are subjected to parameters variations due to aging and temperature is disclosed; resultant distortion is reduced or eliminated via a real time calibration.
This application is a continuation-in-part application of U.S. patent application Ser. No. 13/630,146 filed on Sep. 28, 2012, which in turn claims the benefit of U.S. Provisional Patent Application No. 61/652,743, filed on May 29, 2012, U.S. Provisional Patent Application No. 61/657,999, filed on Jun. 11, 2012 and U.S. Provisional Patent Application No. 61/665,592, filed on Jun. 28, 2012; this application is a continuation-in-part application of U.S. patent application Ser. No. 13/776,068 filed on Feb. 25, 2013, which is a continuation-in-part application of U.S. patent application Ser. No. 13/630,146 filed on Sep. 28, 2012, which in turn claims the benefit of U.S. Provisional Patent Application No. 61/652,743, filed on May 29, 2012, U.S. Provisional Patent Application No. 61/657,999, filed on Jun. 11, 2012 and U.S. Provisional Patent Application No. 61/665,592, filed on Jun. 28, 2012; U.S. patent application Ser. No. 13/776,068 further claims benefit from U.S. Provisional Patent Application No. 61/658,015 filed on Jun. 11, 2012, U.S. Provisional Patent Application No. 61/658,009 filed on Jun. 11, 2012, U.S. Provisional Patent Application No. 61/665,600 filed on Jun. 28, 2012 and U.S. Provisional Patent Application No. 61/671,417 filed on Jul. 13, 2012, all of which are incorporated herein by reference in their entirety.
The term “hybrid MIMO RDN” as used herein is defined as a MIMO system that employs two or more antennas per channel (N is the number of channels and K is the total number of antennas and K>N). This architecture employs a beamformer for each channel so that two or more antennas are combined for each radio circuit that is connected to each one of the channels.
In hybrid MIMO RDN receiving systems, when the phases of the received signals from each antenna are properly adjusted or tuned with respect to one another, the individual signals may be combined and result in an improved SNR for the receiving system.
FIG. 2 shows an implementation whereby each antenna of an antenna array 201 as shown in FIG. 1 is enhanced by adding a means to adjust the weight of its signal (amplitude and phase) 202 prior to applying it to a passive RF combiner 203. In one embodiment the phase and amplitude of each antenna's signal is measured by the radio and baseband 204, which performs a “channel estimation” function of the received signal.
The measurements allow the system to determine in advance the phase and optionally the amplitude of each signal prior to applying it to 203 in order to accomplish constructive signal combining To accomplish this effectively, it is important the system predicts the consequences of each setting. For this reason a calibration of phase and amplitude for all operational settings and for all operating conditions such as frequency and temperature is required. This invention describes the design and methods to provide a unit calibration to provide values to be used during operation to adjust the settings.
FIG. 1 is a high level illustration of a simple MIMO receiving system with antenna array and RDN according to some embodiments of the invention;
FIG. 2 is an implementation for one embodiment of the system allowing setting of the weight of the signal from each antenna and channel estimation according to some embodiments of the invention;
FIG. 3 is a high level illustration of one embodiment allowing calibration of the gain from each antenna using a test generator and channel estimation. It also presents an alternative approach that replaces the test signal generator and channel estimator with a network analyzer according to some embodiments of the invention;
FIG. 4 is diagram of circuitry allowing calibration of the gain from each antenna separately according to some embodiments of the invention;
FIG. 5 is an implementation for one embodiment of the system allowing setting of the weight of the signal from each antenna and providing operational bypass of the RF combiner for channel estimation according to some embodiments of the invention;
FIG. 6 is a flowchart showing a method for calibration using the embodiment of FIG. 2 according to some embodiments of the invention;
FIG. 7 is a flowchart showing a method for calibration using the embodiment of FIG. 5 according to some embodiments of the invention; and
FIG. 8 is an implementation for one embodiment of the system allowing setting of the weight of the signal from each antenna and providing operational bypass of the RF combiner for channel estimation employing an RF signal combiner with a reconfigurable combining ratio according to some embodiments of the invention.
FIG. 1 is a high level block diagram illustrating a system according to embodiments of the present invention. A MIMO receiving system set in a hybrid MIMO RDN configuration is shown. In the hybrid MIMO RDN configuration, baseband module 110 receives N branches and is configured to operate, on the baseband level, in accordance with any known or legacy MIMO receiving scheme. The system includes a radio distribution network 130 (RDN) connected to baseband module 110 via radio circuits 20-1 to 20-N. RDN 130 includes at least one beamformer such as 120-1 and 120-N, being fed by two or more antennas such as 50-1-1 to 50-N-KN, so that a total number of antennas in the system is greater than the number of the channels. Baseband module 110 further includes digital signal processing (DSP) modems 112 and an RF signal processing and control module 114 and a memory 116, wherein control module 114 is configured to tune RDN 130 and also to calibrate the beamformers as will be explained in detail below.
FIG. 2 shows an implementation whereby each antenna of an antenna array 201 of the RDN beamformer system of FIG. 1 (only one beamformer is shown in FIG. 2) is enhanced by adding the ability to adjust the weight of its signal (amplitude and phase) 202 prior to applying it to a passive RF combiner 203. In one embodiment the phase and amplitude of each antenna's signal is measured by the radio and baseband 204, which performs a “channel estimation” function of the received signal.
The system, as illustrated in FIGS. 2, 5 and 8 that are explained in detail below, comprises a multiple-input-multiple-output (MIMO) receiving system comprising a MIMO baseband module having N branches (only one branch shown in FIGS. 2, 5 and 8) or inputs associated with radio channels (20-1 to 20-N as shown in FIG. 1) and a radio distribution network (RDN) connected to the MIMO receiving system.
The RDN which includes a beamformer may be fed by two or more antennas, so that a total number of antennas in the system is K, wherein K is greater than N.
The beamformer may include at least a combiner configured to combine signals coming from the antennas into a combined signal.
The diagram of FIG. 2 shows the elements of an RDN beamforming system. In operation the phases and (optionally) amplitudes of the signals from the antennas in array 201 are adjusted to ensure optimum alignment using the weighting adjustments provided by circuits 202. Factors that affect the ability to achieve the alignments may include:
Accuracy of the phase and amplitude adjustment settings of the weighting circuits 202
Variation of the phase and amplitude versus operational conditions of frequency and temperature
Variation of phase when adjusting amplitude and variation of signal amplitude when adjusting phase
Phase shift and loss differences through RF combiner 203 experienced by the antenna signals. This can be incidental due to combiner tolerances or difference in trace lengths or intentional by design (e.g., quadrature combiners introduce a 90 degree phase shift for some paths.)
Inspection of FIG. 2 shows we can measure the end-to-end gain by applying a signal to each input separately (Input1 through Inputk) and measure and record its change in phase and amplitude. The equipment to do this is shown in FIG. 3. The RF test signal from the Signal Generator 301 is routed through the Test RF Circuits 400. As shown in the embodiment of FIG. 4, the signal can be applied individually to each input (Input1 through Inputk). The flow chart of FIG. 6 outlines the steps to employ the embodiment shown in FIG. 3 using the internal channel estimation circuits to measure the voltage (amplitude and phase) for each signal path.
Often, during operation, it is desirable to bypass the combiner when performing channel estimation of the signals received by each antenna. This is because the combiner 203 introduces a combining loss of 1/k to each input signal when the others are not present. For this reason the circuit of FIG. 5 or similar have been proposed. Single pole switches 508 and multi-throw switch 509 are added to route each signal in order to bypass the combiner 503. When the signals are bypassed (switch position B), the measured phase and amplitude by the channel estimation will be different than when the signals are routed through the combiner. For this reason the calibration tables generated must take these differences into account in order for “bypass” measurements to be applicable to setting the weights when operating in the “non-bypassed” configuration.
The flowchart of FIG. 6 describes for one embodiment the steps to be followed to generate the calibration tables when using a test configuration as shown in FIG. 3. In this figure we see a baseline is established with the weight settings of 202 at maximum gain and the “zero” phase setting. Since the gain for each of the k antenna paths is measured under these conditions, a comparison of these measurements shows what offsets must be applied in order to align the signals to add constructively in the combiner 203. Subsequent measurements determine the accuracy of the gain and amplitude weight settings and the interaction between the settings (i.e., the phase shift variation for different gain settings and the amplitude (gain) variations when adjusting the phase).
According to the flowchart of FIG. 6, the method may include operations such as configuring equipment as shown in FIG. 3 and setting frequency and level of Test Generator (or alternatively the Network Analyzer as required and Test RF Circuits for Output to Input 610; setting the gain of the RDN to maximum and Phase to zero degrees 620; measuring and recording the voltage and phase at the Output port using the Internal Channel Estimator or alternatively the Network Analyzer 630; adjusting the gain of the RDN from maximum to minimum with Phase at zero degrees and measuring and recording for each gain setting (or a selected subset) the voltage and phase at the Output port as before 640; adjusting the gain of the RDN to maximum and for each possible phase setting measuring and recording the voltage and phase at the Output port as before 650; exercising all switches and measuring amplitude and phase of each antenna at each state 660; repeating for other measurement conditions of frequency and temperature 670; and loading calibration data in UE 680.
The flowchart of FIG. 7 describes the same factors for the circuit of FIG. 5 that FIG. 6 does for the circuit of FIG. 2 with the addition of a measurement with the combiner 503 bypassed. This allows the system to perform channel estimation on received signals with the advantage of bypassing the combiner and to apply the proper settings operationally without the combiner bypassed.
FIG. 8 describes an embodiment of the invention for which the calibration procedure described in FIG. 7 is also applicable. The structure of RDN 800 may include antennas 801 which are fed into variable gain amplifiers and phase shifters 802 and then to splitters 808 from which some of the signals are combined by combiner 803 to be later combined with other outputs of splitters 808 in a combiner 809, exhibiting a total gain 807, and into a channel estimator 804. In operation the combiner coupling is adjusted to accommodate a different number of antennas to be combined to avoid combiner losses such as 805 and 806 as described in U.S. patent application Ser. No. 13/776,068.
In general each combiner configuration introduces a different coupling ratio and phase shift to its input signals. This means the calibration procedure described in FIG. 7 must be repeated for each combiner configuration to be employed during unit operation.
According to some embodiments, the RDN circuits of 500 in FIGS. 5 and 800 in FIG. 8 may be contained within a module such as an integrated circuit (IC). In this case the calibration configuration as shown in FIG. 3 and the processes outlined in FIG. 6 and FIG. 7 may be employed during module manufacture.
In one embodiment the calibration values may be stored within module in nonvolatile memory 116 to be retrieved when the RDN module is installed in user equipment (UE). A UE may be referred herein in a non-limiting manner as any device used directly by an end-user to communicate. A UE can be a hand-held telephone, a laptop computer equipped with a mobile broadband adapter, or any other suitable device. It is obvious the size of memory needed will depend on the RDN configuration and precision required.
In one embodiment the RDN of FIG. 5 will provide five phase shifters each with four phase shifts of ninety degree increments. It would be possible to measure the phase shift provided by each phase setting with a resolution of thirty degrees. In this case the calibration would be required to measure twenty values of four bits each plus one word for the combiner bypass routing for each phase shifter and twice that total for two RDN's supporting MRC or 2×2 MIMO. In general the size of the memory required will depend on the module configuration and precision required as well as sufficient memory to store coefficients as necessary to characterize the module performance over operational conditions such as frequency and temperature.
In another embodiment calibration is performed in real time over the air during normal system operation using channel estimation. The need for such a procedure stems out of manufacturing limitations as well as of human operational mode:
(a) RF circuitry calibration procedures of many Wireless devices are based on plugging probes between the radios ports and the antennas, in many cases leaving the antennas themselves un-calibrated; that lack of full calibration is sometimes due to the cost of radiated test.
(b) Human handling of a wireless device is often involving touching the area where an antenna is located, inadvertently modifying both amplitude and phase. Proximity sensor or other sensing means like VSWR monitoring may be used in order to trigger real time field calibration procedure.
Real time calibration can offer remedy in both of the above cases.
During normal operation the transmitter (e.g. base station) transmits reference signals that allow the channel to be estimated. The estimated channel is the overall channel from the transmit antenna to the beamformer output. During calibration only one of the beamformer antennas is activated. Therefore, the overall channel comprises an external channel from the transmit antenna to the single active beamformer antenna, and an internal channel which is the signal path from the active beamformer antenna to the beamformer output. The internal signal path varies depending on the selected weights (amplitude and phase) and configuration (bypass or non-bypass).
Let Ri, i=1 . . . k, be the number of internal paths to be calibrated from beamformer input i to its output, and p(i,j), i=1 . . . k, j=1 . . . Ri, be the internal paths from input i to the output. Internal path p(i,j) can be expressed as AINT(i,j)ejφ INT(i,j) , wherein AINT(i,j) and φINT(i,j) are respectively amplitude and phase of internal path p(i,j). Similarly, the external channel from the transmit antenna to beamformer input i is expressed as AEXT(i)ejφ EXT(i) . Therefore, the overall channel comprising the external channel and an internal path p(i,j) is given by AEXT(i)ejφ EXT(i) AINT(i,j)ejφ INT(i,j) .
A channel ratio Ratio (i, j1, j 2) between two channels, both including the same external channel from the transmit antenna to same input i, but having distinct internal paths p(i, j1) and p(i, j2), j1=1 . . . Ri, j2=1 . . . Ri, j1≠j2, is defined as:
Ratio ( i , j ⁢ ⁢ 1 , j ⁢ 2 ) = A EXT ⁡ ( i ) ⁢ ⅇ jφ EXT ⁡ ( i ) ⁢ A INT ⁡ ( i , j ⁢ ⁢ 1 ) ⁢ ⅇ jφ INT ⁡ ( i , j ⁢ ⁢ 1 ) A EXT ⁡ ( i ) ⁢ ⅇ jφ EXT ⁡ ( i ) ⁢ A INT ⁡ ( i , j ⁢ ⁢ 2 ) ⁢ ⅇ jφ INT ⁡ ( i , j ⁢ ⁢ 2 ) = A INT ⁡ ( i , j ⁢ ⁢ 1 ) ⁢ ⅇ jφ INT ⁡ ( i , j ⁢ ⁢ 1 ) A INT ⁡ ( i , j ⁢ ⁢ 2 ) ⁢ ⅇ jφ INT ⁡ ( i , j ⁢ ⁢ 2 ) = A INT ⁡ ( i , j ⁢ ⁢ 1 ) A INT ⁡ ( i , j ⁢ ⁢ 2 ) ⁢ ⅇ j ⁡ ( φ INT ⁡ ( i , j ⁢ ⁢ 1 ) - φ INT ( i , j ⁢ ⁢ 2 )
Since in general the external channel is time varying, for measurements done at instants n and m the channel ratio may be expressed showing the time dependencies as:
Ratio ⁢ ( i , j ⁢ ⁢ 1 , j ⁢ 2 ) = A EXT ⁡ ( i ) ⁡ ( n ) ⁢ ⅇ jφ EXT ⁡ ( i ) ⁢ ( n ) ⁢ A INT ⁡ ( i , j ⁢ ⁢ 1 ) ⁢ ⅇ jφ INT ⁡ ( i , j ⁢ ⁢ 1 ) A EXT ⁡ ( i ) ⁡ ( m ) ⁢ ⅇ jφ EXT ⁡ ( i ) ⁢ ( m ) ⁢ A INT ⁡ ( i , j ⁢ ⁢ 2 ) ⁢ ⅇ jφ INT ⁡ ( i , j ⁢ ⁢ 2 ) ⁢ = ~ ⁢ A INT ⁡ ( i , j ⁢ ⁢ 1 ) ⁢ ⅇ jφ INT ⁡ ( i , j ⁢ ⁢ 1 ) A INT ⁡ ( i , j ⁢ ⁢ 2 ) ⁢ ⅇ jφ INT ⁡ ( i , j ⁢ ⁢ 2 ) = A INT ⁡ ( i , j ⁢ ⁢ 1 ) A INT ⁡ ( i , j ⁢ ⁢ 2 ) ⁢ ⅇ jφ INT ⁡ ( i , j ⁢ ⁢ 1 ) - φ INT ( i , j ⁢ ⁢ 2 )
According to some embodiments, the calibration procedure may include the following stages:
1. Define the calibration time slots. During the calibration time slots only a single beamformer antenna is activated and the system performs momentarily calibration function in addition to regular receiver functions. Since Ratio(i, j1, j2) is a ratio between two different channels, two separate channel estimations are required for estimating Ratio(i, j1, j2); therefore, in order to minimize variations in the external channel the time slots may be grouped in pairs for back to back channel estimation and more accurate estimation of Ratio(i, j1, j2).
2. Set i=1.
3. Select a path p(i, j1) from beamformer input i to its output as anchor.
4. Using channel estimation compute Ratio(i, j1, j2) for fixed j1 (selected in step 3 as anchor) and j2=1 . . . Ri, j2≠j1, and store the computed values in the calibration table.
5. Repeat steps 3 and 4 for i=2 . . . k.
6. Repeat steps 2 to 5 periodically and average the measurements.
If an indication of channel mobility is available, it may be optionally used to add weights in the average: low mobility measurements may receive higher weights than high mobility measurements. If an indication of SINR is available, it may be optionally used to add weights in the average: high SINR measurements may receive higher weights than low SINR measurements. The temperature and frequency may be added to the calibration table, in which case the measurements may be averaged separately for different temperatures and frequencies. In some embodiments, the calibration table may be stored in non-volatile memory.
In some embodiments the real time calibration is performed only when slow fading is identified by a channel mobility detection procedure.
During regular RDN operation, the calibration table is used to correct channel estimation values before they are used for RDN weight settings.
a multiple-input-multiple-output (MIMO) receiving system comprising a MIMO baseband module having N branches;
a radio distribution network (RDN) connected to the MIMO receiving system with an antenna array of K antennas, the RDN comprising at least one beamformer with k weighting circuits and one radio frequency (RF) signal combiner configured to combine signals coming from the antennas feeding the respective beamformer into a combined signal, wherein k, K and N are positive integers and wherein k is greater than 1 and K is greater than N, wherein the RDN is tuned for optimal performance using channel estimation of individual contributing antennas of the RDN;
a signal processing control module configured to: tune the K antennas, wherein the tuning is carried out based on RDN calibration data; and generate said RDN calibration data, based on at least one of: offline and real time procedures for eliminating or reducing systematic errors and unpredictable errors,
wherein the calibration is carried out as follows:
using a given beamformer antenna for receiving, while disconnecting other antennas in the same beamformer;
channel estimating the signals received from a serving transmitting station: for each possible phase and gain setting, for each possible switch setting, and for each possible combiner;
selecting as an anchor or reference point one of said settings, and comparing the channel estimations for all other selected settings to the anchor's channel estimation;
creating a calibration table using a deviation between the anchor setting and other settings; and
repeating the calibration process for all antennas and for all beamformers in the RDN.
2. The system according to claim 1, wherein the calibration table is calculated in the following manner:
dividing each of the various possible routing's channel estimation measurements by the channel estimation value measured for the anchor setting, resulting in a plurality of complex numbers expressing the power ratio and phase difference between each possible routing setup and the anchor setup.
3. The system according to claim 2, wherein said calibration is carried out several times or periodically and the results are averaged.
4. The system according to claim 3, wherein mobility indication is used for applying weights to said calibration measurements average calculation, and wherein higher mobility values are assigned lower weights to said average process.
5. The system according to claim 3, wherein signal to interference plus noise ratio (SINR) measurements are used for applying weights to said calibration measurements average calculation, and wherein higher SINR values are assigned higher weights to said average process.
wherein a real time calibration is performed by using the base station transmission as a calibration reference signal, as follows:
(a) upon activation of a user equipment (UE), a mobility detection is performed, until slow fading is identified;
(b) the RDN is then reduced to first antenna only, via toggling of various switches incorporated inside the RDN, and the measurement of amplitudes and phases at different positions is performed;
(c) next, a second antenna only is activated and the procedure is repeated, and then the next one till all participating RDN antennas are tested;
(d) the real-time calibration procedure of both amplitudes ratios and phases differences is performed a number of times that is sufficient to reduce via averaging, the impact of the external channel fluctuation between time slots; and the procedure is repeated periodically.
receiving radio frequency (RF) signals via a radio distribution network (RDN) having an antenna array of K antennas, the RDN comprising at least one beamformer with k weighting circuits and one RF signal combiner configured to combine signals coming from the antennas feeding the respective beamformer into a combined signal, wherein k is greater than 1 and K is greater than N;
conveying the combined signal to a multiple-input-multiple-output (MIMO) receiving system comprising a MIMO baseband module having N branches;
generating RDN calibration data, based on both offline and/or real time procedures that eliminate or significantly reduce systematic errors and unpredictable errors introduced during normal operation,
wherein the calibration is carried out by:
8. The method according to claim 7, wherein the calibration table is calculated by:
9. The method according to claim 8, wherein said calibration is carried out several times or periodically and the results are averaged.
10. The method according to claim 9, wherein mobility indication is used for applying weights to said calibration measurements average calculation, and wherein higher mobility values are assigned lower weights to said average process.
11. The method according to claim 9 wherein signal to interference plus noise ratio (SINR) measurements are used for applying weights to said calibration measurements average calculation, and wherein higher SINR values are assigned higher weights to said average process.
wherein calibration tables are created by measurement with external test equipment to account for a variation of the phase and gain for each signal as settings of gain and phase are changed when the combiner is bypassed and not bypassed.
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US201261671417 true 2012-07-13 2012-07-13
US13630146 Continuation-In-Part US8654883B2 (en) 2012-05-29 2012-09-28 Systems and methods for enhanced RF MIMO system performance
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US14102539 Active US8885757B2 (en) 2012-05-29 2013-12-11 Calibration of MIMO systems with radio distribution networks
US (1) US8885757B2 (en)
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US20140098902A1 (en) 2014-04-10 application
Kildal et al. 2011 Threshold receiver model for throughput of wireless devices with MIMO and frequency diversity measured in reverberation chamber
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