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Timestamp: 2017-03-31 01:03:14
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Matched Legal Cases: ['Application No. 2502924', 'Application No. 2503532', 'Application No. 2515167', 'Application No. 2503530', 'Application No. 2487817', 'Application No. 2484313', 'Application No. 2442400', 'Application No. 2491259', 'Application No. 2491259', 'Application No. 2503432', 'Application No. 200410100591', 'Application No. 03757359', 'Application No. 03794510', 'application No. 05254902', 'Application No. 07075745', 'Application No. 04256234', 'Application No. 03742400', 'Application No. 03777694', 'Application No. 03742393', 'Application No. 03774848', 'Application No. 03777627', 'Application No. 03742393', 'Application No. 03774848', 'Application No. 02728894', 'Application No. 03757359', 'Application No. 07075745', 'Application No. 164482', 'Application No. 2004', 'Application No. 20026115', 'Application No. 092129644', 'Application No. 092117948', 'Application No. 092129498', 'art 1', 'Application No. 092129629']

Patent US7639759 - Carrier to noise ratio estimations from a received signal - Google PatentsSearch Images Maps Play YouTube News Gmail Drive More »Sign inPatentsTechniques for measuring the carrier to noise ratio (CNR) in a received digital signal are disclosed. The methods can operate on a received digital signal, such as a layered modulation signal used in a satellite television system. The CNR measurement can be made at the output of a carrier recovery loop...http://www.google.com/patents/US7639759?utm_source=gb-gplus-sharePatent US7639759 - Carrier to noise ratio estimations from a received signalAdvanced Patent SearchTry the new Google Patents, with machine-classified Google Scholar results, and Japanese and South Korean patents.Publication numberUS7639759 B2Publication typeGrantApplication numberUS 10/913,927Publication dateDec 29, 2009Filing dateAug 5, 2004Priority dateApr 27, 2001Fee statusPaidAlso published asCA2515167A1, CA2515167C, EP1624598A1, US20050008100Publication number10913927, 913927, US 7639759 B2, US 7639759B2, US-B2-7639759, US7639759 B2, US7639759B2InventorsErnest C. ChenOriginal AssigneeThe Directv Group, Inc.Export CitationBiBTeX, EndNote, RefManPatent Citations (105), Non-Patent Citations (96), Referenced by (9), Classifications (37), Legal Events (2) External Links: USPTO, USPTO Assignment, EspacenetCarrier to noise ratio estimations from a received signal
US 7639759 B2Abstract
Techniques for measuring the carrier to noise ratio (CNR) in a received digital signal are disclosed. The methods can operate on a received digital signal, such as a layered modulation signal used in a satellite television system. The CNR measurement can be made at the output of a carrier recovery loop or a timing recovery loop in a demodulator. Alternately, the CNR measurement can be made when the received signal is digitized in an analog to digital (A/D) converter at base-band by the demodulator.
This is a continuation-in-part application and claims the benefit under 35 U.S.C. Section 120 of the following commonly-assigned U.S. utility patent application, which is incorporated by reference herein:
Utility application Ser. No. 09/844,401, filed Apr. 27, 2001, by Ernest C. Chen, entitled “LAYERED MODULATION FOR DIGITAL SIGNALS,” issued Apr. 24, 2007 as U.S. Pat. No. 7,209,524.
It has been proposed that a layered modulation signal, transmitting non-coherently both upper and lower layer signals, can be employed to meet these needs. See Utility application Ser. No. 09/844,401. In backwards compatible implementations, the lower layer signal is transparent or “invisible” to the upper layer signal, the primary signal distribution layer, thereby providing backward compatibility with legacy satellite receivers. Such layered modulation systems allow higher information throughput with backwards compatibility. However, even when backward compatibility is not required (such as with an entirely new system), layered modulation can still be advantageous because it requires a TWTA peak power significantly lower than that for a conventional 8PSK or 16QAM modulation format for a given throughput.
Layered modulation (LM) reconstructs the upper layer signal and removes it from the received signal to leave a lower-layer signal. Lower layer signal demodulation performance requires good signal cancellation, which in turn requires the reconstructed signal to include accurate amplitude and phase effects from signal propagation path, filter and low noise block (LNB). Values of these parameters change from system to system and therefore must be estimated for each system.
A major difficulty in the implementation of the layered modulation techniques disclosed in Utility application Ser. No. 09/844,401, filed Apr. 27, 2001, by Ernest C. Chen, entitled “LAYERED MODULATION FOR DIGITAL SIGNALS,” was that the upper layer signal required excessive satellite TWTA power, beyond the current levels for a typical continental United States (CONUS) coverage. The present invention minimizes the required powers to levels of current typical TWTA power limits. Therefore, there is no need to wait for TWTA power technology to further develop before layered modulation can be implemented.
A description of the processes performed in the encoding and decoding of video streams, particularly with respect to MPEG and JPEG encoding/decoding, can be found in Chapter 8 of “Digital Television Fundamentals,” by Michael Robin and Michel Poulin, McGraw-Hill, Hill, 1998, which is hereby incorporated by reference herein.
Layered modulation applications include backwards compatible and non-backwards compatible applications. “Backwards compatible” in this sense, describes systems in which legacy receivers 500 are not rendered obsolete by the additional signal layer(s). Instead, even though the legacy receivers 500 are incapable of decoding the additional signal layer(s), they are capable of receiving the layered modulated signal and decoding the original signal layer. In these applications, the pre-existing system architecture is accommodated by the architecture of the additional signal layers. “Non-backwards compatible” describes a system architecture which makes use of layered modulation, but the modulation scheme employed is such that pre-existing equipment is incapable of receiving and decoding the information on additional signal layer(s).
s UL ( t ) = f U ( M U exp ( j ω U t + θ U ) ∑ m = - ∞ ∞ S Um p ( t - mT ) ) + f L ( M L exp ( j ω L t + θ L ) ∑ m = - ∞ ∞ S Lm p ( t - mT + Δ T m ) ) + n ( t ) where, MU is the magnitude of the upper layer QPSK signal and ML is the magnitude of the lower layer QPSK signal and ML<<MU. The signal frequencies and phase for the upper and lower layer signals are respectively ωU, θU and ωL,θL. The symbol timing misalignment between the upper and lower layers is ΔTm. p(t−mT) represents the time shifted version of the pulse shaping filter p(t) 414 employed in signal modulation. QPSK symbols SUm and SLm are elements of
{ exp ( j n π 2 ) , n = 0 , 1 , 2 , 3 } · f U ( · ) and ƒL(·) denote the distortion function of the TWTAs for the respective signals.
Ignoring ƒU(·) and ƒL(·) and noise n(t), the following represents the output of the demodulator 1004 to the FEC decoder 1002 after removing the upper carrier:
As previously discussed the present invention may also be used in “non-backward compatible” applications. In a first example embodiment, two QPSK layers 1104, 1110 are used each at a code rate of ⅔. The upper QPSK layer 504 has a CNR of approximately 4.1 dB above its noise floor 1106 and the lower QPSK layer 1110 also has a CNR of approximately 4.1 dB. The total code and noise level of the lower QPSK layer 1110 is approximately 5.5 dB. The total CNR for the upper QPSK signal 1104 is approximately 9.4 dB, merely 2.4 dB above the legacy QPSK signal rate 6/7. The capacity is approximately 1.74 compared to the legacy rate 6/7.
FIG. 11B depicts the relative power levels of an alternate embodiment wherein both the upper and lower layers 1104, 1110 are below the legacy signal level 1102. The two QPSK layers 1104, 1110 use a code rate of ½. In this example, the upper QPSK layer 1104 is approximately 2.0 dB above its noise floor 1106 of approximately 4.1 dB. The lower QPSK layer has a CNR of approximately 2.0 dB and a total code and noise level at or below 4.1 dB. The capacity of this embodiment is approximately 1.31 compared to the legacy rate 6/7.
In one embodiment, instructions implementing the operating system 1208, the computer program 1210, and the compiler 1212 are tangibly embodied in a computer-readable medium, e.g., data storage device 1220, which could include one or more fixed or removable data storage devices, such as a zip drive, floppy disc drive 1224, hard drive, CD-ROM drive, tape drive, etc. Further, the operating system 1208 and the computer program 1210 are comprised of instructions which, when read and executed by the computer 1202, causes the computer 1202 to perform the steps necessary to implement and/or use the present invention. Computer program 1210 and/or operating instructions may also be tangibly embodied in memory 1206 and/or data communications devices 1230, thereby making a computer program product or article of manufacture according to the invention. As such, the terms “article of manufacture”, “program storage device” and “computer program product” as used herein are intended to encompass a computer program accessible from any computer readable device or media.
The present invention provides for the measurement of CNR and signal compensation for tracked carrier phase and phase modulation in a CONUS satellite signal distribution. An exemplary embodiment of the invention provides a measurement of the CNR of a received signal by processing the output from the carrier recovery loop, generating schematic representations of the signal nodes, wherein the CNR measures the points of disparity (“fuzziness”) surrounding the signal nodes and comparing the value of the input signal CNR to a predetermined degradation by impairments.
The CNR measurement can be made at the output of the carrier recovery loop. The signal is further compensated for the tracked carrier and phase modulation. The real signal produces points which deviate from the ideal signal node. In a two-dimensional “scatterer-frame”, these points appear as “fuzziness” around each of the signal nodes. The CNR measurement is essentially a measurement of the size of the apparent “fuzziness” around the signal nodes. Processing from the carrier recovery loop output to measure the CNR can produce a very accurate measurement (e.g. on the order of 0.1 dB at a CNR of approximately 7 dB). This is particularly true if the constellation is constructed after layered modulation processing subtracts the received signal from the decoded nodes, resulting in virtually no uncoded symbol errors. The measurement takes into account all impairments right before the signal is FEC decoded.
In other embodiments, the CNR measurement can be determined at the timing recovery loop output. In this case, the signal is sampled at tracked symbol times (“top of the baud”). The amplitudes are stabilized and the carrier phase modulation remains. In processing the measurement there is no need to run a coherent carrier recovery loop. Thus, the impairment effect of carrier recovery loop is not included. Determining the CNR measurement at the timing recovery loop output should be more accurate than a measurement determined at the A/D output and before timing recovery loop (e.g. on the order of 0.2 dB at a CNR of approximately 7 dB). However, if the downstream carrier recovery loop shows poor performance, simulations show that the CNR measurement will be less accurate but still useful in many applications.
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