Source: https://patents.google.com/patent/DE69836880T2/en
Timestamp: 2020-08-12 19:29:38
Document Index: 626511070

Matched Legal Cases: ['arts 220', 'arts 220', 'arts 220', 'art 220', 'art 220', 'art 220', 'art 220', 'arts 342', 'arts 220', 'arts 220']

DE69836880T2 - Integrated semiconductor circuit with test mode and normal operating current paths - Google Patents
Integrated semiconductor circuit with test mode and normal operating current paths
DE69836880T2
DE69836880T2 DE69836880T DE69836880T DE69836880T2 DE 69836880 T2 DE69836880 T2 DE 69836880T2 DE 69836880 T DE69836880 T DE 69836880T DE 69836880 T DE69836880 T DE 69836880T DE 69836880 T2 DE69836880 T2 DE 69836880T2
DE69836880T
DE69836880D1 (en
Hironori Hirakata-shi Osaka Akamatsu
Akira Yawata-shi Kyoto Matsuzawa
Kazuko Uji-shi Kyoto Nishimura
1997-05-23 Priority to JP13336997 priority Critical
1997-05-23 Priority to JP13336997 priority
1998-05-22 Application filed by Panasonic Corp filed Critical Panasonic Corp
2007-03-08 Publication of DE69836880D1 publication Critical patent/DE69836880D1/en
2007-05-24 Publication of DE69836880T2 publication Critical patent/DE69836880T2/en
2018-05-23 Anticipated expiration legal-status Critical
239000004065 semiconductors Substances 0.000 title claims description 43
The The invention relates to semiconductor integrated circuits comprising a circuit for use in self-diagnosis and self-extinction.
at a CMOS integrated circuit consisting of a PMOS circuit and an NMOS circuit, only one of this switched to the on state when the integrated CMOS circuit is in operation, and therefore is the loss of energy low. If errors and / or defects, such as bridging between wires, in integrated CMOS circuits occur, the power consumption in the order of magnitude increased by a few digits. This is detected in procedures such as quiescent current test and IDDQ test exploited by increases in the value of electric current at the time of testing of large-scale integrated circuits, the from integrated CMOS circuits are observed.
With the reduction of the supply voltage of highly integrated circuits became the least possible in terms of reducing energy consumption so far the reduction of Vt (threshold voltage) in MOS transistors, the arranged in integrated CMOS circuits, strongly demanded, to ensure a satisfactory operating speed. However, with low Vt MOS transistors, there is an increase in the Leakage in the standby state. To cope One such problem has been two techniques for reducing Energy consumption during of the standby period. A technique sets a configuration for integrated CMOS circuits to increase the Vt of respective MOS transistors in the standby state by semiconductor wafer voltage control a, d. H. a so-called configuration of integrated CMOS circuits with variable threshold voltage (VT-CMOS). On the other hand, the other technique the aforementioned configuration of integrated MT-CMOS integrated circuit CMOS circuits, in other words, a configuration integrated CMOS circuits is provided, in which a Circuit of low Vt MOS transistors during the Standby period using MOS transistors with high Vt is switched to the blocking state. The configuration integrated MT-CMOS circuit points opposite the configuration of the integrated VT CMOS circuit has the advantage that they switch faster from operating mode to standby mode can reach.
The has the configuration described above integrated MT-CMOS circuit however, the problem on that is the amount of leakage that is in the standby mode occurs, since each of the lower Vt forms an integrated CMOS circuit. The share of an increasing Amount of abnormal current coming from abnormal states (error and / or defects) is therefore reduced, thereby it becomes difficult to detect errors at trial time. Performing Including tests the IDDQ test is difficult.
The Document EP-A0 283 186 relates to a chip recovery circuit, which is formed on a semiconductor integrated circuit, equipped with a variety of functionally equivalent circuit blocks is. The recovery circuit allows for chip recovery through Deactivation of a circuit block in which abnormal operating characteristics be recorded. The remaining circuit blocks can then be used. A switching device corresponds to each circuit block to power from the power line to the corresponding circuit block. A shift control device corresponds to each shift device, to selectively activate the activation of the corresponding switching device to control.
In Considering the problems with the techniques described above The prior art has made the invention. Consequently, there is one Object of the invention therein, a novel integrated semiconductor circuit to provide the MOS circuits consisting of transistors with low Vt are built in, wherein the semiconductor integrated circuit increases the amount of electric current that can be detected by an abnormal State, which takes place in a MOS circuit is caused.
This is characterized by the features according to the statement in the independent Claim reached. Further advantageous embodiments of the present invention become dependent Claims set forth.
A Circuit of low Vt MOS transistors being tested is divided into a large number of circuit blocks and MOS transistors with high Vt to turn off the circuit blocks during normal standby mode operation also used at the time of testing for leakage current. With other words is for Each circuit block sets up a circuit current in each circuit block through a high VtM transistor a test circuit is passed.
One Circuit block being tested is using a MOS transistor with high Vt, which is used to shut off power in the Standby time is selected, and a feed stream in a circuit of low Vt MOS transistors will be for each chosen Circuit block detected and the detected supply current is given a reference value compared to determine if it is acceptable or not. When The consequence of such an arrangement is the number of circuit blocks at a time during tested in test mode operation, testing including IDDQ testing can be implemented by increasing the supply current due to faults and / or defects in lower MOS transistors Vt is detected.
One Circuit block is tested for presence or absence of an error therein by leakage current test, and if the circuit block is faulty, then becomes such a faulty circuit block replaced by a previously prepared spare circuit block.
When Sequence of such an arrangement for replacing a faulty circuit block a replacement circuit block makes it possible to deal with existing errors correct. This provides improvements in the yield of integrated Semiconductor circuits ready. In addition, because of leakage current is judged per circuit block, a circuit block in which a leakage current flows, which is bigger as the reference value, easily specified. This invention provides a semiconductor integrated circuit used for circuit block evaluation, fault analysis and to other similar ones Capable of operations is.
1 shows in block form a semiconductor integrated circuit belonging to the invention.
2 is a circuit diagram showing the details of a test object circuit, ie a test candidate, and an in 1 shown circuit block switching part shows.
3 is a schematic that details the in 1 shown test circuit shows.
4 is a circuit diagram of a circuit in which a reference current value is determined on the basis of measured values.
5 FIG. 12 is a circuit diagram showing a partial view of a circuit resulting from the addition of a spare block circuit to the circuit of FIG 2 is formed.
A semiconductor integrated circuit of the invention will be described with reference to the accompanying drawings. First, reference is made 1 which shows an exemplary structure of a semiconductor integrated circuit (SIC) of the invention. 210 is a scan register. The scan register 210 is a circuit block selector which can be operated to receive block selection data BS and to sequentially transmit the received data BS after a clock CP to provide respective block selection signals S11-S61. 220A and 220B are circuit block switching parts. The circuit block switching parts 220A and 220B are circuit block switching means for (a) applying a circuit voltage VCIR to a test object circuit 230 as a test object composed of circuit blocks including a circuit block AB and a circuit block TG, and (b) switching paths of circuit currents in the circuit blocks between the paths of detected currents I11-I61 and a path to ground GND in response to the test enable signal TE, the block select signals S11-S61 and the operation select signal / OP ("/" indicates a negative logic signal) 230 may comprise SRAM, ROM and logic circuits formed on the same chip. The test object circuit 230 is a circuit that can be divided into a plurality of circuit blocks, ie, the aforementioned circuit blocks AB-TG. 240 is a test circuit. The test circuit 240 is a test device for disconnecting the paths of each detected current I11-I61 during normal mode operation, generating a reference current based on a received reference voltage VREF, making a comparison between a received detected current and the generated reference current, and providing a block test result T, if a specified condition is met. 250 is a register circuit. The register circuit 250 is a memory means for receiving the block test result T and sequentially shifting the block test result T to generate parallel block test data D11-D61, and for providing the test data D as needed, such as when necessary for specifying a defective circuit block.
The operation of the SIC of 1 will now be described below. The scan register 210 sequentially transmits the block selection data BS consisting of a bit string such as [HIGH LOW LOW LOW LOW, .....] of which one bit in the most significant bit position is the only HIGH bit, and sequentially places one of the block selection signals S11 -S61 in the state HIGH for forwarding to the circuit block switching parts 220A and 220B according to the clock CP. Upon receiving the test enable signal TE at HIGH level, the circuit block switching parts switch 220A and 220B the paths of the circuit currents in the circuit blocks AB-TG. In particular, the switching parts lead 220A and 220B to the test circuit 240 a detected current I corresponding to a circuit block receiving a block selection signal S HIGH (for example, when the signal S11 is HIGH, then the detected current I11 becomes the circuit 240 fed). On the other hand, upon receiving the test enable signal TE at the LOW level, all the circuit currents I11-I61 in the test object circuit become 230 to the test circuit 240 supplied when the Betriebsauswählsignal / OP is HIGH. When the operation selection signal / OP is LOW, all the circuit currents I11-I61 flow out of the circuit 230 out to Earth GND. During test mode operation of a particular circuit block, the test circuit will turn off 240 based on the received reference voltage VREF provides a reference current as a reference and provides the block test result T indicating that the circuit block is not operating normally when a detected current with respect to the circuit block exceeds the value of the reference current. In addition, in normal mode operation, the paths of the (detected) circuit currents are set in the disconnected state. The register circuit 250 receives and sequentially shifts the result T to generate the block test data D11-D61 to indicate which of the circuit blocks is not operating normally. The register circuit 250 provides the block test data D11-D61 as needed. The operation described above enables either a circuit current flowing in a circuit block selected from all the circuit blocks AB-TG or a plurality of circuit currents selected in a plurality of circuit blocks selected from all the circuit blocks AB-TG. flow, check.
2 shows the test object circuit 230 and the circuit block switching parts 220A and 220B in 1 , The test object circuit is made up of circuit blocks that form an address buffer 231 , a first to nth memory block 232 - 233 and a clock generator 234 contain. The circuit voltage VCIR is applied to each of these circuit blocks. Each circuit block is provided with a current path through which its circuit current is delivered to GND during normal mode operation and another circuit path into which its circuit current is delivered as a sensed current I during test mode operation. Each circuit block is a CMOS integrated circuit constructed of a low Vt NMOS transistor and a low Vt TLN and TLP PMOS transistor. High Vt THP11-THP-61 PMOS transistors together form the circuit block switching part 220A , Each high Vt THP11-THP-61 PMOS transistor operates as a power supply line switching device that can separate a respective current path (ie, a respective normal mode operation current path) to GND. On the other hand, each high Vt THN11-THN-61 NMOS transistor functions as a current supply switching device switching a respective current path (ie, a respective test mode operation current path) to the test circuit 240 can separate. Low Vt NMOS transistors QN11-QN-61 and low Vt QP11-QP-61 PMOS transistors are driving devices for switching the high Vt MOS transistors and, together with the high Vt NMOS transistors, form THN11-THN- 61, the circuit block switching part 220B ,
The operation of the circuit block switching part 220A and the operation of the circuit block switching part 220B are described in different situations. In the first situation, the test enable signal TE is HIGH. In this case, all of the lower Vt QN11-QN-61 NMOS transistors turn on, and at the same time all the lower Vt QP11-QP-61 PMOS transistors turn off. As a result, the block selection signals S11-S61 are supplied to the gates of the high-Vt MOS transistors in the circuit blocks from which a circuit block which has received a block selection signal S at HIGH is selected. In such a selected circuit block, its high Vt THN and THP NMOS and PMOS transistors are turned on and off, respectively. As a result, the selected circuit block is connected to its test mode operation current path while being disconnected from its normal mode operation current path. A circuit current in the selected circuit block becomes a corresponding sensed current I, which then passes through the test mode operation current path to the test circuit 240 is supplied. At this time, circuit currents in the remaining other circuit blocks which have received block selection signals S at LOW are output to ground GND, and therefore these circuit blocks have no effect on the testing.
On the other hand, if the test enable signal TE is LOW, all of the lower Vt QN11-QN61 NMOS transistors turn off and at the same time all the lower Vt QP11-QP61 PMOS transistors turn on. As a result, the operation selection signal / OP is supplied to the gates of the high-Vt MOS transistors. In the second situation SIGNAL TE is LOW and SIGNAL / OP is HIGH. In this case, all of the NMOS transistors with high Vt THN11-THN61 turn on and at the same time all high Vt THP11-THP61 PMOS transistors turn off. As a result, all the circuit blocks are updated with their respective test modes driving current paths are connected and disconnected from their respective normal mode operation current paths. Consequently, the detected currents I11-I61, that is, the circuit currents of all the circuit blocks, become the test circuit by means of the test mode operation current paths 240 fed. These current paths are separated separately at their respective feed target and the total circuit current in the test object circuit 230 ie the amount of current in the test object circuit 230 is consumed, becomes zero. In the third situation SIGNAL TE is LOW and SIGNAL / OP is LOW. In this case, all NMOS transistors with high Vt THN11-THN61 turn off and at the same time all high Vt THP11-THP61 PMOS transistors turn on. As a result, all the circuit blocks are connected to the normal mode operation current paths and are disconnected from the test mode operation current paths and all circuit currents are delivered to ground so as to allow normal mode operations. The signal combination of the first situation is used for test mode operations. The signal combination of the second situation is used for normal standby mode operations. The signal combination of the third situation is used for normal mode operations.
3 is a schematic of the in 1 shown test circuit 240 , A reference current determining circuit 241 is a signal supply means for supplying current designation signals L1-L4 on the basis of parallel data of bits in which the number of logic one bits is one (in other words, the remaining other bits are all logical zero bits) to determine a reference current value. The circuit 241 is from a reference current destination memory 242 for storing the parallel data. 243 is a reference current generating circuit. The circuit 243 reference value generating means for determining a reference current from the received reference voltage VREF on the basis of the signals L1-L4. The circuit 243 provides the thus determined reference current. 244 is a comparison circuit. The comparison circuit 244 is a comparator. The comparison circuit 244 disconnects the paths of sensed currents during normal mode operation while the circuit 244 on the other hand, during the test mode operation receives a detected current and a reference current to make a comparison between them, and provides the block test result T HIGH when the detected current exceeds the reference current. The reference current generating circuit 243 is formed of reference current determining resistors RR1-RR5 and MOS transistors Q1-Q5. The comparison circuit 244 is made up of partial voltage resistors R1A, R2A, R1B, R2B, MOS transistors Q6 and Q7 and a comparator 245 educated. The resistors R1A and R1B have the same resistance. The resistors R2A and R2B have the same resistance. A bias voltage VA is used to adjust the value of current flowing in each MOS transistor Q6 and Q7 and to turn off both MOS transistors Q6 and Q7 during normal mode operation. In contrast, a bias voltage VB is used to determine the value of current in the comparator 245 flows, adjust and the comparator 245 during normal mode operation.
The operation of the test circuit 240 is described. The test circuit 240 For example, the reference voltage VREF is supplied to operate as a power supply voltage only during test mode operation. Since in normal mode operation VREF is not connected to the test circuit 240 is applied and all the MOS transistors Q6 and Q7 and the comparator 245 are latched, the paths of the detected currents I11-I61 from the test object circuit 230 separated. As a result, the total circuit current in the test object circuit 230 ie the amount of electricity in the circuit 230 is consumed during normal standby mode operation. On the other hand, during the test mode operation, the standard supply voltage Vdd becomes the test object circuit 230 as VREF to the test circuit 240 is also created as a VCIR to the test object circuit 230 created. The reference current determining circuit 241 performs based on the parallel data of four bits stored in the memory 242 are stored, the signals L1-L4, of which the signal L3 is HIGH. The signal L3 at HIGH causes its corresponding MOS transistor Q3 to turn on to divide VREF using a combination of resistors RR1-RR5, and the resulting voltage is applied to the gate of the MOS transistor Q5. In accordance with the received gate voltage, the MOS transistor Q5 amplifies a current supplied from VREF to be forwarded to the comparison circuit 244 , The comparison circuit 244 Connects to an input terminal of the comparator 245 a target voltage generated by the amplified current and the resistors R1A and R2A, and applies to the second input terminal of the comparator 245 a detected voltage generated by the received detected current and the resistors R1B and R2B. The comparator 245 performs a comparison between the target voltage and the detected voltage applied to its respective input terminals, and provides the block test result T HIGH when the detected voltage is greater than the target voltage. The comparison of a sensed voltage and a desired voltage allows the comparison of a detected current and a reference current. By supplying Vdd as VREF and by adequately determining VCIR that goes to the test object circuit 230 is fed in addition, the acceleration gungsstesten be facilitated by applying an excessive voltage as VCIR. In this case, to achieve external application of VCIR and VREF from outside the semiconductor integrated circuit during test mode operation, terminals for these voltages may be provided to the semiconductor integrated circuit.
In the above description, the circuit generates 243 Reference currents of four different values based on four different voltages obtained by voltage division of VREF. The number of voltage levels generated by voltage division of VREF can be increased using the following structure for further division of the reference current value.
For example, an arrangement may be made in which three reference current determination memories 242 to be provided. The number of data elements is increased up to 12, with four data elements in each memory 242 get saved. The number of combinations of the resistors RR1-RR4 and the MOS transistors Q1-Q4 is increased to 12. As a result, each data element is assigned a respective combination of a resistor RR and a MOS transistor Q. Here, in order to determine a reference current with rough accuracy, (i) the resistance of each of a first group of four resistors RR1-RR4 is adjusted so that voltage division of these resistors RR1-RR4 can be performed in a wide voltage range; (ii) the resistance of each of a second group of four resistors RR1-RR4 is adjusted to allow voltage division of these resistors RR1-RR4 to be performed in a medium voltage range; and (iii) adjusting the resistance of each of a third group of four resistors RR1-RR4 so that voltage division of these resistors RR1-RR4 can be performed in a narrow voltage range. In other words, these three register groups function as a low-accuracy resistance group, a medium-precision resistance group, and a high-precision resistance group, respectively. Likewise, the twelve data elements in the memories 242 supplied as low-precision data, as medium-precision data, and as high-precision data to their respective MOS transistors. As a result, the twelve MOS transistors based on the from the memories 242 read out 12-bit data either in the on state or in the off state. Consequently, resistors of the three resistor groups selected by the respective MOS transistors and the resistor RR5 are connected in series, and VREF is voltage-divided by these resistors in series. In this way, a voltage resulting from the voltage division of VREF, ie, a voltage which can be highly accurate, is applied to the gate of the MOS transistor Q5 so as to allow a reference current to assume a further divided fine value. When it is judged from the characteristics of a test object circuit and from the required accuracy that coarsely accurate testing is sufficient, only the four low-precision resistors are used to obtain a reference current. In contrast, if high accuracy testing is required, then all low, medium, and high accuracy resistor groups are used to achieve a reference current. The testing is performed on the basis of the obtained reference current. Each of the detected currents I11-I61 is compared by value with such obtained reference current and by the comparison circuit 244 assessed.
Of the Aspect of the structure described above is integrated To provide semiconductor circuits that are tested quickly can, if Low accuracy testing can be done because only the four resistances low accuracy, and also high on demand Accuracy can be tested.
The number of reference current destination memories 242 , which can store four bits each, is three, allowing a reference current to accept twelve different values. However, the number of reference current destination memories is not limited to three, and the number of bits for which each memory is constructed is not limited to four.
As described above, the reference currents are input to the reference current determination memory 242 certainly. With reference to the 3 and 4 As a modified version of the reference current determining technique, a reference current determining structure based on an actually measured leakage current value will now be described below.
4 FIG. 12 is a circuit diagram of a circuit for use in determining a reference current value based on a measured leakage current value. FIG. In the following description will be the same elements that also in 3 are shown with the same reference numerals and the description thereof is omitted.
A test circuit 340 from 4 results from the addition of a structure for sequentially increasing the value of reference current to the test circuit 240 from 3 , A reference current determining circuit 341 is a signal feeder for providing the current designation signals L1-L4 on the basis of parallel data consisting of bits in which the number of logic one bits is only one (in other words, all the remaining other bits are logical zero bits) to determine a current reference value. The circuit 341 is composed of a reversing circuit NOT of three NOT circuits, a NOT circuit INV, NAND circuits NA1-NA3, an NMOS transistor Q8 and a reference current destination memory 342 built up. The memory 342 is a memory device for storing bits, all at the beginning of the operation of the circuit 341 are at logical zero. With the operation of the circuit 341 the store works 342 as a shift register and generates and stores parallel data. A current determination clock ICLK, via the NMOS transistor Q8 to the memory 342 is applied, is a tact to the memory 342 to enable performing sequential shift operation. A reference current determination signal IDET which is sent to the memory 342 is a signal consisting of a bit string of which one bit in the most significant bit position is the only HIGH bit (that is, all the remaining other bits are LOW). RESET indicates a reset signal and the LOW state of the signal RESET at the time when the clock ICLK is not to the memory 342 is supplied, feeding of the clock ICLK to the memory starts 342 ,
The operation of the reference current determining circuit 341 is described. A reference circuit block, which is the circuit block in which the circuit configuration is estimated to be likely to undergo leakage, is preselected, and a leakage current flowing in the reference circuit block is measured. A circuit current included in the reference circuit block as the test object circuit 230 is flowing from the circuit block switching parts 220A and 220B from 3 via a test mode operation current path to the comparison circuit 244 fed. The comparison circuit 244 compares the circuit current as a detected current I and a reference current, and provides the block test result T HIGH when the detected current exceeds the reference current.
As the signal IDET of 4 a series signal [HIGH LOW LOW LOW ..., LOW] is sequentially supplied in accordance with the clock ICLK on the basis of current designation data [1 0 0 0 ... 0] of a bit string, one of which is in the most significant bit position the only logical bit is and all the remaining other bits are logical zero bits. As the signal RESET becomes a LOW only at the beginning of the operation of the circuit 341 fed in the other situations, a HIGH is supplied. In other words, at the beginning of the operation of the circuit 341 is the signal RESET LOW, so that the output of the NAND circuit NA3, that is, an input of the NAND circuit NA2, is set to HIGH.
A situation is considered where the block test result T is LOW, that is, a situation where a detected current from the reference circuit block falls below the reference current. In such a case, since the result T is supplied to an input of the NAND circuit NA1 and a signal which is a reversal of the result T is supplied to the second input of the NAND circuit NA1, the output of the NAND circuit NA1 as the second input of the NAND circuit NA2 regardless of the result T HIGH. Since all inputs of the NAND circuit NA2 are high, the output of the NAND circuit NA2 is therefore LOW. The inverter INV provides a high as its output, turning on the MOS transistor Q8. The ICLK clock is then sent to memory 342 applied. In the store 342 the signal IDET is sequentially shifted after the clock ICLK.
Next, consider a situation in which a HIGH of the signal IDET is sequentially shifted based on the most logical one bit of current designation data, resulting in the block test result T HIGH, in other words, a situation considered a detected current exceeds the reference current. In this case, the block test result T is supplied HIGH to the one input of the NAND circuit NA1, and thereafter the block test result T delayed and reversed by the invert circuit NOT from HIGH to LOW is supplied to the second input of the NAND circuit NA1 , In other words, only for a short period from the time when the result T is supplied to the one input of the NAND circuit NA1, to the time when the delayed inverse result T is applied to the second input of the NAND circuit NA1 is supplied to both inputs of the NAND circuit NA1 each with HIGH. As a result, the circuit NA1 only supplies a LOW as its output to an input of the NAND circuit NA2 for a short period of time. In this case, the NAND circuit NA2 supplies a high as its output regardless of the level of signals received from the NAND circuit NA3. Due to this, the output of the inverter INV is low and therefore the NMOS transistor Q8 turns off. Supplying the clock ICLK to the memory 342 comes to a standstill. Consequently, in the memory 342 the signal IDET, which has been shifted sequentially, switched on. In other words, data representing the detected current from the Be block, in this case in the form of parallel data in the memory 342 held. Thereafter, if the value of the detected current falls below the value indicative of a fatal defect such as a short circuit due to bridging between wires, the parallel data is then sent to the circuit as SIGNALS L1-L4 243 fed. Such an arrangement allows the value of the sensed current from the reference block to be used as a leakage current reference.
A LOW may be provided as a SIGNAL RESET at the time a comparison between sensed current and reference current occurs again. This puts the memory 342 again in the operation start state and the supply of the clock ICLK can be started.
To In the present modified version, a leakage current that is in a circuit block flows, which is estimated in consideration of the circuit configuration, that he is most likely the Occurrence of leakage current is subject, actually measured and a leakage current, which flows in a different circuit block becomes judged by using such a measured value as a reference. The use of such an actually measured value makes it possible to perform Tests without even if there is a change in the value of leakage due, for example, to process fluctuation, gives an overly drastic reference value to take over. The present modified version provides semiconductor integrated circuits ready, which can be manufactured with a stable inquiry rate.
The present modified version can be applied to a specified circuit block to be applied in consideration of the circuit configuration estimated is that he is very likely to be affected by leakage. If, in such a case, such a circuit block as normal working, it can be assumed that the remaining other circuits also work normally. This will be integrated Semiconductor circuits with the participation of a lower number of test steps can be tested.
When Candidate for Measurement, that is as a reference circuit block, either a circuit block on the same chip or a circuit block on a different one Chip to be used. For example, if at a certain Chip that is near is formed of a periphery of a semiconductor wafer, it is estimated that he most likely is subject to the occurrence of leakage, one in such a chip trained circuit block is used as a reference circuit block become.
in the Special allows this if one of circuit blocks in a different chip with the same structure as a test object circuit block as a Reference circuit block selected will, more accurately of testing, since they are nearly identical to each other at the leakage current value are.
In addition, can as a reference circuit block, a circuit block adjacent to a test object circuit block. With In other words, a circuit block that is assumed to be that he is working under production conditions that match the manufacturing conditions a test object circuit block were highly similar, was manufactured, used as a reference circuit block. This represents an integrated Semiconductor circuit prepared from circuit blocks with a more uniform Leakage current distribution is made. Such an arrangement is for Example when manufacturing integrated semiconductor circuits in masses effective. additionally the test configuration can be simplified as a leakage current, in a test object circuit block flows, and another flowing in an adjacent circuit block, always with each other be compared.
When a circuit block having a configuration different from a test object circuit block is used, it may cause the problem that a difference in the leakage current value occurs between these two circuit blocks due to the configuration difference. In this case, an arrangement may be made to test for a threshold shift by the comparison circuit 244 from 3 to prevent a normal leakage current value difference from being judged as a fault.
According to the present modified version, the supply of the clock ICLK becomes the memory 342 disconnected when the block test result T enters the HIGH state. The same arrangement can be applied to testing, such as an IDDQ test. In other words, the circuit structure of 4 even when used in the course of an IDDQ test on the semiconductor integrated circuit of 1 an error is detected. In this case, at the time when the block test result T enters the HIGH state, that is, when a detected current from the reference circuit block exceeds the reference current, the shifting operation of the scanning register is performed 210 from 1 interrupted to cancel the test. This eliminates the need to take time to test after detecting a fault, thus achieving reductions in total test time.
Now take reference 5 , therein is shown another modified version of the semiconductor integrated circuit of the present invention. It is preferable that even if the above-described test technique discovers that a semiconductor integrated circuit includes a defective circuit block therein, such defective semiconductor integrated circuit can be fully restored to normal operation and used as a product instead of being disposed of. In the present modified version, an in 5 is used to provide a semiconductor integrated circuit which can be reset to normal operation even when judged non-normal. 5 FIG. 13 is a circuit diagram showing a part of a circuit as a result of adding a spare block circuit to the circuit of FIG 2 shows. In the following description will be the same elements that also in 2 are shown with the same reference numerals and the description thereof is omitted.
A spare block circuit 400 from 5 is a switching device for switching a defective circuit block to a spare circuit block. The circuit 400 has a spare memory block 235 , a high Vt THP3Y PMOS transistor, a high Vt THN3Y NMOS transistor, a low Vt QN3Y NMOS transistor, a low Vt QP3Y PMOS transistor, a switching NMOS transistor SW3Y, fuses F1-Fn, and a NAND circuit NA4.
The spare memory block 235 is a memory block for replacement by a defective memory block having the same structure as each of the first to n-th memory blocks 232 - 233 (M1-Mn). The transistors THP3Y and THN3Y are power supply line switching devices. Upon entering the on-state, transistor THP3Y assures a current path for the operation of the spare memory block 235 , Upon entering the on-state, transistor THN3Y assures a current path for the test operation of the spare memory block 235 , The transistors QN3Y and QP3Y are driving elements for switching the transistors THP3Y and THN3Y to the level of the test enable signal TE.
Each fuse F (F1-Fn) is a circuit separator consisting of a fuse resistor R (R31-R3n) and an NMOS transistor N (N31-N3n). As the NMOS transistors N31-N3n, transistors having a small gate width-to-gate length ratio (ie, high-resistance transistors in which low current flows) are used. The NAND circuit NA4 is a logic gate for providing an alternative block switching signal SCB formed of a NAND logic signal on the basis of the output of each fuse F1-Fn. The transistor SW3Y is a switching device for opening and closing a current path for the operation of the spare memory block 235 after the level of SIGNAL SCB received from the NAND circuit NA4.
Each of the memory blocks M1-Mn in the structure with the spare memory block 235 are identical, is a memory block for electrical replacement by the replacement block 235 if it is determined to be a bad memory block. Between the node of the first memory block 232 and the transistor THN31 and the transistor THP31, the transistor SW31 is connected, the gate of which is coupled to the output of the fuse F1. In the same way is between the node of the nth memory block 233 and the transistor THN3n and the transistor THP3n, the transistor SW3n whose gate is coupled to the output of the fuse Fn. The remaining other memory blocks are identical in the circuit structure to the first and n-th memory blocks. The gates of the transistors SW31-SW3n are respectively coupled to the inputs of the NAND circuit NA4.
Regarding 5 Now, the memory block replacement operation of the spare block circuit will be described below 400 described.
First, consider a situation where each memory block M1-Mn operates normally. In this case, no processing is performed on each fuse resistor R31-R3n. Consequently, the outputs from the fuses F1-Fn assume respective values generated by voltage division of VCIR by the transistors N31-N3n taken as high resistance resistors and the fuse resistors R31-R3n. These outputs are therefore all connected to a level very close to HIGH. As a result, all the transistors SW31-SW3n of the memory blocks M1-Mn are put into the on-state, and the output of the NAND circuit NA4, ie, SIGNAL SCB becomes LOW so as to turn on the transistor SW3Y of the spare memory block 235 off. As a result, current paths for the operation of the memory blocks M1-Mn are saved and a current path for the operation of the spare memory block 235 is disconnected, whereupon each memory block enters the operating state for operation.
Next, consider a situation where the first memory block 232 is assessed as a defective memory block. In this case, a defective circuit block may be specified from data in the reference current determination memory when the block test result T becomes HIGH. A fuse resistor with respect to the first memory block 232 , ie the fuse resistor R31, is disconnected therefrom. Such disconnection of the fuse resistor R31 may be performed using techniques such as high voltage application and lasers which do not affect the other elements. As a result, the output of the fuse F1 is pulled down to GND by the transistor N31, which is taken as a high-resistance resistor and is tied to the LOW level. The transistor SW31 of the first memory block 232 then turns off. On the other hand, since the output of the fuse F1 becomes LOW (ie, an input of the NAND circuit NA4), the NAND circuit NA4 provides HIGH as the SIGNAL SCB. Due to this, the transistor SW3Y of the first memory block turns on 235 one. While the current path for the operation of the first memory block 232 (ie the bad memory block) is disconnected, becomes the current path for the operation of the spare memory block 235 secured. As a result, the spare memory block operates 235 in place of the first memory block 232 ,
To In the present modified version, a memory block, the is determined to be faulty by testing through a spare memory block replaced. This provides semiconductor integrated circuits that can be reset to normal operation by such replacement.
The transistor SW3Y of the spare memory block 235 is controlled based on the output of the fuses F1-Fn using a NAND circuit. A single spare memory block is provided for a plurality of regular memory blocks. If a defective memory block exists in the regular memory blocks, such a defective memory block is replaced by the spare memory block.
The Description has been made with respect to memory blocks. However, in the case different types of circuit blocks, such as logic circuits, Replacement logic circuits are arranged.
at In the above description, a spare circuit block is provided for n circuit blocks. Each circuit block may be associated with a respective replacement circuit block be equipped. A variety of replacement circuit blocks may be appropriate for one Variety of circuit blocks to be provided. In the latter case, as the plurality of spare circuit blocks, identical circuit blocks to be provided. Replacement circuit blocks of different types, the from circuit blocks, like memory blocks, of the same type can be provided.
Further, circuit block replacement may be performed whenever a HIGH (error) is provided as the block test result T in testing each circuit block. Alternatively, stack circuit block replacement may be performed in which circuit blocks that apply a HIGH to the register circuit 250 all replaced at a time by replacement circuit blocks.
In addition is this is constructed so that only one or more circuit blocks, the most likely will not work normally, with appropriate Spare circuit blocks be equipped.
MOS transistors high Vt arranged to make circuit blocks MOS transistors with low Vt in standby mode, become to select of a test object circuit block used from the circuit blocks. A circuit current flowing in the selected circuit block becomes detected. If the detected current exceeds the reference value, it is determined that such a selected circuit block not working normally. As a result of such an arrangement, the Number of circuit blocks, which are being tested at a time without re-deploying of additional switching devices limited, whereupon testing, such as IDDQ testing, on circuits that are formed of low Vt MOS transistors can.
Of Further, a circuit block that does not operate normally will a replacement circuit block replaced. This provides semiconductor integrated circuits. even if an error occurs in it, not more immediately Disposal be subjected to and reset to normal operation can be thereby improving the production yield.
leakage current is judged by circuit block, which makes it possible a circuit block with a leakage current that is larger as a reference, easy to specify under circuit blocks. This provides semiconductor integrated circuits that are simpler Circuit block rating, error analysis and so on.
An arrangement may be made in which only the circuit block switching parts 220A and 220B and the test object circuit 230 be provided on a chip and a specific contact point is used to SIGNAL S11-S61 from outside a semiconductor wafer on which the chip is formed apply. In addition, it is possible to examine the detected currents I11-I61 from outside the wafer. As a result, testing, such as IDDQ testing, on circuits consisting of low Vt MOS transistors is achieved without requiring increases in chip area.
In addition to the above it is possible a variety of circuit blocks at the same time by checking the block selection data BS of bits, of which a variety of desired Bits set to HIGH, used and given a reference value adequate is set. As a result of such an arrangement, the number of the bushings of a circuit block test, since it is sufficient that Single test of the circuit blocks only then done when this simultaneous testing gives an error indication. Of Further it becomes possible testing on circuit blocks in the same situation in which they are actually used.
In addition to the above, each circuit block may be connected to the test circuit 240 and the block test result T and the parallel input can be applied to the register circuit 250 be applied. This arrangement makes it possible to increase the number of circuit blocks that can be tested simultaneously.
At the in 3 The structure shown has the reference current determination memory 242 only one type of parallel data. An arrangement may be made in which a memory capable of storing a plurality of different elements of parallel data is provided to select between them. Further, without forming a memory on a chip, parallel data for the circuit 243 from outside a semiconductor wafer on which the chip is formed.
In The above description ensures the on state of the transistors THP11-THP61 current paths, the while of the normal mode operation, and the on-state NMOS transistors THN11-THN61 secures electricity routes during of the test mode operation, the transistors THP11-THP61 and THN11-THN61 be arranged on the side to which currents flow from the circuit blocks, and Signals TE and S are positive logic; but these are not as restrictive be considered. For example, in each circuit block, a current path, supplied by the VCIR with a high Vt PMOS transistor instead of a transistor THP and with a high Vt NMOS transistor instead of a transistor THN equipped to switch between a circuit path during the Normal mode operation is used, and a circuit path, the while of test mode operation is used to toggle.
The structure of the present invention is used to make disconnection from or connection to a power supply circuit and, in addition, to access a circuit block at the time of actual use. When a semiconductor integrated circuit receives the address of a defective circuit block at the time of actual use, a spare circuit block must be selected for the defective circuit block. It is assumed here that there is a faulty circuit block. In such a case, data indicating the faulty circuit block is in the register circuit 250 are held, the held data and the decoded address of an access object circuit block are compared. If there is an indication of coincidence, it means that the access object circuit block is not operating normally. Therefore, an arrangement may be made in the circuit structure in advance so that a spare circuit block may become an object for access instead of the defective circuit block.
A semiconductor integrated circuit comprising: a test object circuit ( 230 ) consisting of a plurality of circuit blocks ( 231-234 ), each containing MOS transistors having a first threshold voltage, and being subjected to a test; characterized by: power supply line switching means (THN-11-THN61, THP11-THP61) disposed in a power supply line of each of the circuit blocks and constructed of MOS transistors having a second threshold voltage greater than the first threshold voltage around the path switching current flowing in each of the circuit blocks to a normal mode operation current path or a test mode current path while disconnecting a circuit block connected to its test mode current path from its normal mode operation current; a circuit block selector ( 210 ) for selecting a desired one of the plurality of circuit blocks to execute a switching of the current path to the test mode current path during the test mode of operation; and a test device ( 240 ), which at the time the value of a current flowing on the switched test mode current path in the selected circuit block exceeds a predetermined reference value, generates a specified signal (T) indicating that the selected circuit block does not works normally.
A semiconductor integrated circuit according to claim 1, wherein said test object circuit ( 230 ) is constructed of an integrated CMOS circuit.
A semiconductor integrated circuit according to claim 1, wherein said circuit block selector ( 210 ) includes a sample register for receiving a signal and for sequentially shifting the received signal to produce a block selection signal used to select the desired circuit block.
A semiconductor integrated circuit according to claim 1, wherein the test device ( 240 ) a reference value generating device ( 243 ) for generating the predetermined reference values respectively corresponding to the plurality of circuit blocks.
A semiconductor integrated circuit according to claim 4, wherein the test device ( 240 ) further includes: voltage dividing means (R1B, R2B; R1A, R2A) for receiving the current flowing on the switched current path in the desired circuit block and for dividing a received reference voltage to produce the reference value equal to the value of the received current is; and a memory device ( 242 ) for acquiring required data at the reference voltage division.
A semiconductor integrated circuit according to claim 4, wherein said reference value generating means ( 243 ) Includes means (RR1-RR4) for determining the accuracy of the reference values respectively corresponding to the plurality of circuit blocks.
A semiconductor integrated circuit according to claim 4, wherein said reference value generating means ( 243 ) Comprises power supply lines (VREF) for generating the reference values extending from the power supply lines (VCIR) for supplying voltage to the plurality of circuit blocks (FIG. 231 - 234 ).
Integrated semiconductor circuit according to Claim 7, which further comprises: a terminal for supplying Voltage to power supply lines for the supply from voltage to the plurality of circuit blocks from outside the semiconductor integrated circuit; and a connector for feeding from voltage to the power supply lines for the generation the reference values from outside the integrated semiconductor circuit.
A semiconductor integrated circuit according to claim 1, wherein the test device ( 240 ) includes means for simultaneously testing a plurality of circuit blocks that are triggered by the circuit block selector (10). 210 ) from the plurality of circuit blocks ( 231 - 234 ) to be selected.
A semiconductor integrated circuit according to claim 1, further comprising: a spare circuit block ( 235 ) having the same circuit structure as at least one of the plurality of circuit blocks ( 231 - 234 ) Has; and switching means (SW31-SW3n) which, when a specified signal (T) is generated, indicating that a circuit block in the plurality of circuit blocks having the same structure as the spare circuit block does not operate normally, the defective circuit block replace with the replacement circuit block.
A semiconductor integrated circuit according to claim 1, wherein the test device ( 240 ) further includes a breaker interrupting the test mode operation when a specified signal (T) is generated indicating that the selected circuit block is not operating normally.
DE69836880T 1997-05-23 1998-05-22 Integrated semiconductor circuit with test mode and normal operating current paths Expired - Lifetime DE69836880T2 (en)
JP13336997 1997-05-23
DE69836880D1 DE69836880D1 (en) 2007-03-08
DE69836880T2 true DE69836880T2 (en) 2007-05-24
ID=15103125
DE69836880T Expired - Lifetime DE69836880T2 (en) 1997-05-23 1998-05-22 Integrated semiconductor circuit with test mode and normal operating current paths
EP (1) EP0880172B1 (en)
KR (1) KR100506667B1 (en)
DE (1) DE69836880T2 (en)
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AT300741T (en) * 1996-06-05 2005-08-15 Imec Inter Uni Micro Electr High resolution power supply system
1998-05-22 DE DE69836880T patent/DE69836880T2/en not_active Expired - Lifetime
1998-05-22 KR KR10-1998-0018525A patent/KR100506667B1/en not_active IP Right Cessation
1998-05-22 EP EP19980109356 patent/EP0880172B1/en not_active Expired - Lifetime
EP0880172B1 (en) 2007-01-17
EP0880172A3 (en) 2002-04-03
EP0880172A2 (en) 1998-11-25
DE69836880D1 (en) 2007-03-08
KR100506667B1 (en) 2005-09-26
KR19980087302A (en) 1998-12-05
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