Source: https://patents.google.com/patent/JP2561040B2/en
Timestamp: 2020-06-02 06:32:14
Document Index: 668061186

Matched Legal Cases: ['art 2', 'art 3', 'art 4', 'art 5', 'art 7', 'art 8', 'art 9']

JP2561040B2 - Capacitance sensor capacitance change detection circuit and detection method thereof - Google Patents
Capacitance sensor capacitance change detection circuit and detection method thereof
JP2561040B2
JP2561040B2 JP6292859A JP29285994A JP2561040B2 JP 2561040 B2 JP2561040 B2 JP 2561040B2 JP 6292859 A JP6292859 A JP 6292859A JP 29285994 A JP29285994 A JP 29285994A JP 2561040 B2 JP2561040 B2 JP 2561040B2
JP6292859A
JPH08145717A (en
博之 岡田
1994-11-28 Application filed by 日本電気株式会社 filed Critical 日本電気株式会社
1994-11-28 Priority to JP6292859A priority Critical patent/JP2561040B2/en
1996-06-07 Publication of JPH08145717A publication Critical patent/JPH08145717A/en
1996-12-04 Publication of JP2561040B2 publication Critical patent/JP2561040B2/en
G01L9/12—Measuring steady of quasi-steady pressure of fluid or fluent solid material by electric or magnetic pressure-sensitive elements; Transmitting or indicating the displacement of mechanical pressure-sensitive elements, used to measure the steady or quasi-steady pressure of a fluid or fluent solid material, by electric or magnetic means by making use of variations in capacitance, i.e. electric circuits therefor
BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a capacitance change detecting circuit for a capacitance type sensor in a signal processing circuit of a sensor for detecting a physical quantity by a minute change in capacitance and a detecting method thereof.
2. Description of the Related Art A typical example of a circuit that detects physical phenomena such as pressure and acceleration as fluctuations in capacitance value and converts the fluctuations into electric signals is the "IEEE Cus" of 1983.
tomCircut Conf. Y. E. Park (Y. Park, pp. 380-384).
E. FIG. Park) et al., "An MOS switch"
ched-capacitive readout a
mpliferfor capacitive pr
“Essure sensors”.
The circuit described in this paper is used as a read circuit of a capacitive pressure sensor, and has a temperature of 1 fc at room temperature.
Have a resolution of. Referring to FIG. 5 (a) which shows a circuit diagram of the operation principle of this circuit and FIG. 5 (b) which shows a time chart for explaining the operation, this circuit shows a clock generator 10, a sensor 3 and an input terminal. A feedback control switch (hereinafter referred to as a switching transistor) 42 and a feedback capacitance element 43 are respectively connected in parallel between (-) and the output terminal (+), and the input terminal (+) is connected to the reference voltage Vr.
Of the operational amplifier (hereinafter referred to as a feedback amplifier) 41 connected to the potential of the clock generator 10
The output end of the inverter 11c is connected to one end of the capacitive element 31 of the sensor 3 via the inverters 11a, 11b, and 11c.
The output ends of are connected to one end of the capacitive element 32 of the sensor 3, respectively. The other end of each of the capacitive elements 31 and 32 is connected to the (−) terminal of the feedback amplifier 41, the output end of the feedback amplifier 41 is connected to the terminal SCOUT, and the output end of the clock generator 10 is the gate electrode of the switching transistor 42. The parasitic capacitance Cp13 exists between the wiring connected to the input terminal (−) and the ground potential.
Here, the capacitance Cs of the sensor capacitance element 31 is a variable capacitance that changes according to pressure, and here it represents the sensor capacitance Cs, and the capacitance Cr of the sensor capacitance element 32 is a reference capacitance (hereinafter, referred to as a reference capacitance. The sensor capacitance element 32 is referred to as a reference capacitance element 32), and the sensor 3 produces an amount in which the sensor capacitance Cs fluctuates from the reference capacitance Cr, that is, a capacitance difference (Cs-Cr), depending on the pressure.
According to the above configuration, the clock signal supplied from the clock generator 10 is the inverter 11
is supplied to the sensor capacitance element 31 and the reference capacitance element 32 via a, 11b, 11c and the inverter 12, and the capacitance difference output of the sensor 3 is output to the switching transistor 42.
And the feedback capacitance element 43 are connected to the feedback amplifier 41.
Referring also to FIG. 5B, time t =
At t0, the reference capacitance element 32 and the sensor capacitance element 31
Qr = (reference capacitance Cr × (sensor drive voltage Vp−reference voltage Vr), Qs = (reference capacitance C
s) × (−reference voltage Vr) is accumulated. Therefore, the charge Qt accumulated in the two capacitors is Cr (Vp-Vr)
-CsVr.
Next, at time t = t1, the reset (reset) signal φG goes low, the switching transistor 42 is turned off, and the input / output of the feedback amplifier 41 is opened in terms of direct current.
At time t = t2, the charge Qr = (reference capacitance Cr) × is applied to both ends of the reference capacitance element 32 and the sensor capacitance element 31 while the reset signal φG remains low level.
(−reference voltage Vr), Qs = (reference capacitance Cs) × (sensor drive voltage Vp−reference voltage Vr) are accumulated.
Therefore, the charge Q connected to the two capacitors
t ′ becomes −VrCr + Cs (Vp−Vr), but since the input / output of the feedback amplifier 41 is in an open state, the charge Q0
= Qt−Qt ′ = − Vp (Cs−Cr) is stored in the feedback capacitance element 13.
After all, the output voltage Vscout appearing at the output SOUT of the feedback amplifier 41 is the potential Vscout at which the charge Q0 is accumulated in the feedback capacitance element Vscout =-(charge Q0) /
(Feedback capacitance Cf) stabilizes.
Next, at time t = t3, the reset signal φ
G becomes high level, the feedback amplifier 41 is reset, and the same operation is repeated.
From the above operation relationship, this circuit has an amplitude Vs
A rectangular wave of cout is output, and its value is expressed by Vscout = Vp (Cs-Cr) / Cf ... (1).
As can be seen from the equation (1), the characteristic of this circuit is that it does not depend on the parasitic capacitance Cp13 floating on the input side of the feedback amplifier 41 because the output does not include the parasitic capacitance Cp13. The point is that the fluctuation of the capacity does not affect. Therefore, by using this circuit, it is possible to stably detect a minute capacitance change.
In the conventional capacitance change detection circuit described above, when the switching transistor 42 is switched from on to off (t = t1), the charge Qd accumulated in the gate electrode of this transistor is discharged. It Considering this charge Qd, the sensor 3 and the feedback amplifier 41
The output Vout of the switched-capacitor unit composed of is expressed by the following equation.
Vout = (Vp (Cs-Cr) + Qd) / Cf (2) As can be seen from the equation (2), the charge Qd emitted from the switching transistor 42 is expressed as an offset. I will end up.
Further, since this charge amount is represented by a function of temperature, shape, gate voltage, drain-source voltage, it is extremely difficult to control, and causes temperature drift of the offset voltage.
Further, since the offset voltage and the temperature drift of the feedback amplifier 41 also appear in the output of the switched capacitor circuit, the temperature drift of the offset voltage can be removed even if the output of the switched capacitor unit is amplified and demodulated in the subsequent stage. There was a drawback that I could not.
The object of the present invention has been made in view of the above-mentioned drawbacks, and is to remove the influence of the offset voltage and the temperature drift of the feedback amplifier and the feedback control switching transistor forming the capacitance change detection circuit. An object of the present invention is to provide a highly reliable capacitance change detection circuit for a capacitance type sensor that detects a capacitance difference extremely stably without being affected by ambient temperature and a detection method thereof.
The capacitance change detection circuit for a capacitance type sensor according to the present invention is characterized in that a predetermined sensor regards a physical phenomenon to be detected as a variation in the capacitance value of an electrostatic capacitance, and a difference in the capacitance value. In the capacitance change detection circuit of the capacitance type sensor for converting the output signal to the electric signal by the switched capacitor unit, the first and second sample and hold units having the output signals having the mutual phase difference of 90 degrees output the output signal of the switched capacitor unit. It is to have a detecting means for obtaining the electric signal after obtaining the difference between the respective sampling results after each sampling.
Further, the detection means includes a first sample-hold section for sampling and outputting an output signal of one level of the switched capacitor section in response to a first sampling control signal, and the other level of the switched capacitor section. A second sample-hold section for sampling and outputting the output signal in response to the second sampling control signal, and holding outputs of the first and second sample-hold sections are respectively supplied to the differential amplifier section, In addition, the electrical signal can be output by being differentially amplified.
Further, the switched capacitor section is
It serves as a reference capacitance for taking the difference between the sensor capacitance element driven by the first sensor drive signal and accumulating the variable capacitance of the detection target and the capacitance value of the sensor capacitance element driven by the second sensor drive signal. A reference capacitance element and one input terminal of each of the sensor capacitance element and the reference capacitance element are commonly connected to one input terminal, and a feedback capacitance element and a feedback control switch are connected in parallel from the output terminal while the other is connected. And a feedback amplifier whose input terminal is connected to a predetermined reference potential, and a predetermined timing before the timing when the first sensor drive signal transits from a low level to a high level and the second sensor drive signal transits from a high level to a low level. A first reset period in which the feedback amplifier is activated only during a period, the first sensor drive signal is at a high level, and the second A second reset period in which the feedback amplifier is inactive for a predetermined period when the sensor drive signal is low level, and a transition of the first sensor drive signal from high level to low level and a transition of the second sensor drive signal from low level to high level. A third reset period in which the feedback amplifier is activated only for a predetermined period immediately before the timing, and the first sensor drive signal is at a low level,
A reset signal is supplied to the feedback control switch to repeat a fourth reset period in which the feedback amplifier is inactive for a predetermined period in which the second sensor drive signal is at a high level, in a predetermined period. A feedback amplifier may add the capacitance values of the sensor capacitive element and the reference capacitive element.
Furthermore, there is provided a gain amplification section for amplifying the output of the switched capacitor section, and the signals of the one level and the other level amplified to a predetermined level by the amplification section are the first and the second level signals. It may be supplied to each of the two sample hold units.
Further, a high-pass filter for removing noise in a low frequency band is provided, and the one-level signal and the other-level signal of the output of the gain amplifying unit in which the low frequency band noise is removed by using the high-pass filter are It can also be supplied to the first and second sample and hold sections, respectively.
The feature of the capacitance change detecting method of the capacitance type sensor of the present invention is that a predetermined sensor regards a physical phenomenon to be detected as a variation of the capacitance value of the electrostatic capacitance, and the difference between the capacitance values is electrically detected by the switched capacitor section. In the capacitance change detection method of a capacitive sensor for converting into a signal, after the first and second sample and hold units having output signals having a mutual phase difference of 90 degrees respectively sample the output signals of the switched capacitor unit, Capacitance of a sensor capacitance element that is configured to obtain the electric signal based on a difference between the sampling results by the detection means, and the switched capacitor unit is driven by the first sensor drive signal to accumulate the change capacitance of the detection target. And a reference capacitance for taking the difference between the value and the capacitance value of the sensor capacitance element driven by the second sensor drive signal. When the capacitance value of the irradiation volume element by adding the feedback amplifier means, the feedback amplifier means for adding a capacitance value of said sensor capacitor element and the reference capacitor element;
A first reset period in which the feedback amplifying means is activated for a predetermined time period before the timing at which the first sensor drive signal changes from low level to high level and the second sensor drive signal changes from high level to low level; A second reset period in which the feedback amplifying means is inactive for a predetermined time in which the sensor drive signal is at a high level and the second sensor drive signal is at a low level; and the first sensor drive signal is from a high level to a low level. A third reset period in which the feedback amplifying means is activated for a predetermined time before the timing when the second sensor drive signal transits from the low level to the high level, and the first sensor drive signal is at the low level, and the second sensor drive is performed. The feedback amplifying means is made inactive for a predetermined time when the signal is at the high level By a reset signal that repeats 4 of the reset period in the predetermined predetermined period to supply to the feedback control switch of the feedback amplifier means lies in the so the addition is performed.
By using the configuration of the capacitance change detection circuit of the capacitance type sensor and the capacitance change detection method according to the present invention,
Common mode noise, offset voltage, and temperature drift of the offset voltage that are mixed in the path from the sensor drive unit to the sample hold unit can be canceled by the differential amplification unit inserted after the sample hold unit.
1 (a) is a block diagram showing a first embodiment of the present invention, and FIG. 1 (b) is a circuit diagram of a switched capacitor portion used in the block diagram. Further, FIG. 1C is a timing chart for explaining the operation in the block diagram and the circuit diagram of FIGS.
Referring to FIGS. 1A and 1B, a capacitance change detection circuit according to the present invention includes a logic section 1, a sensor sensor drive section 2 for driving a sensor, a sensor 3, a switched capacitor section 4, and a sample hold section. 5 and 6,
A differential amplifying unit 7, the clock terminal of the logic unit 1 is connected to the input terminal of the sensor driving unit 2, and the sensor driving signal φR output end of the sensor driving unit 2 is one end of the sensor capacitance element 31 of the sensor unit 2. The sensor drive signal φS output terminal is connected to one end of the reference capacitance element 32 of the sensor unit 2,
The other ends of the sensor capacitive element 31 and the reference capacitive element 32 are commonly connected to the input terminal (−) of the feedback amplifier 41 of the switched capacitor unit 4, and the feedback capacitive element 43 and the feedback capacitive element 43 are provided between the input terminal (−) and the output terminal. The switching transistor 42 is inserted in parallel connection, and the input terminal (+) is connected to the potential of the reference voltage Vr.
The output terminal of the switched capacitor section 4 is connected to the sample hold sections 5 and 6, and the respective output terminals thereof are connected to the differential input terminal of the differential amplifier section 7. The capacitance change detection signal is taken out.
Here, the sensor capacitance element 31 and the reference capacitance element 32 represent sensors whose capacitance changes due to mechanical energy such as acceleration and pressure.
1 together with FIGS. 1 (a) and 1 (b).
Referring to (c), at the time t = t0, the switching transistor 42 is conductive only during the period when the reset signal φG is at high level, the feedback portion of the switched capacitor unit 4 is short-circuited, and the sensor drive signal φR is at low level. , The reference voltage Vr and the offset voltage Voff of the feedback amplifier 41, and the output SCOUT of the switched capacitor unit 4 becomes Vscout = Vr + Voff ... (3).
Next, the reset signal φG is switched from the high level to the low level, and the switching transistor 42, which is the feedback section of the switched capacitor section 4, is opened.
At this switching timing, the sensor drive signal φR is still at the low level and the sensor drive signal φS is at the high level, and the switching transistor 42 releases the accumulated charge Qd to the input side of the feedback amplifier 41. Therefore, only the sum of the voltage Vd due to the accumulated charge Qd, the reference voltage Vr, and the offset voltage Voff of the feedback amplifier 41 becomes the switched capacitor unit 4
Output Vscout is Vscout = Vr + Voff + Vd (4).
Next, when t = t1, the reset signal φG is low level, the sensor drive signal φS is low level, and the sensor drive signal φR is high level (amplitude Vp). A charge Qo represented by the following equation is discharged from the capacitive element 32. As described above, the capacitance of the sensor capacitive element 31 is Cs, and the reference capacitive element 3 is
If the capacitance of 2 is Cr, then Qo = (Cs-Cr) Vp ……………………………… (5) Due to this charge Qo, the output shown by the following equation is obtained from the switched capacitor unit 4, It is held by the sample hold unit 5.
Vscout = − (Cs−Cr) Vp / Cf + Vr + Voff + Vd = VSH1 ………………………… (6) The output voltage represented by the equation (6) is output to the sample hold unit 5. During this period, the sampling signal φS1 becomes high level, and therefore the sample hold unit 5 holds the output voltage VSH1 shown by the above equation.
Next, at time t = t2, since the reset signal φG is at the high level, the switching transistor 42 becomes conductive and short-circuited, and the switched capacitor unit 4 is reset and the switched capacitor 42 is reset as at t = t0. The output Vscout of the unit 4 is V as in the equation (3).
r + Voff is output.
Since G is low level, sensor drive signal φR is low level, and sensor drive signal φS is high level, the drive signals of these sensors are in opposite phase to when t = t1, so the output Vscout of the switched capacitor section is expressed by the following equation. Be done.
Vscout = (Cs−Cr) Vp / Cf + Vr + Voff + Vd = VSH 2 ………………………… (7) Further, the output voltage shown by the equation (7) is output to the sample hold unit 6. Since the sampling signal φS2 is at the high level within the period in which the sampling and holding are performed, the sample hold unit 6 holds the output voltage VSH2 expressed by the above equation.
On the other hand, the differential amplifier 7 subtracts the signal voltages output from the two sample and hold units 5 and 6, and the output Vout is given by the following equation.
Vout = VSH1-VSH2 = -2 (Cr-Cr) Vp / Cf (8) As can be seen from the equation (8), the signal obtained at the output of the differential amplifier 7 is Since it can be expressed only by the sensor capacitance Cs, the reference capacitance Cr, the sensor drive signal voltage Vp, and the feedback capacitance Cf, by using the circuit configuration of this embodiment, the influence of the amplifier and the switching transistor forming the switched capacitor section 4 can be completely eliminated. Can be removed.
Here, FIG. 2 showing an example of a logic unit for realizing the timing pulse of FIG. 1 (b) described above.
2, the logic unit 1 has a known circuit configuration, in which the output of the clock oscillator 101 is divided into a predetermined frequency by the counter 102, and the output Qc of one frequency is supplied as the clock signal of the shift register 104. .
The output Qd of the other frequency is further divided by the counter 103 of the next stage, the output Qd is supplied as the data of the shift register 104 and shifted, and the shift outputs Q1 to Q8 of the shift result are output ends Q1 to Q1. Each is output from Q8.
AND108 of the logical product of the result of the logical synthesis of the outputs Q1 and Q3 by the EX-OR 105 and the output Q8.
And outputs the sampling signal φS1 via the buffer 110. The sampling signal φS2 is EX-O.
The logical product of the result of the logical combination in R105 and the signal obtained by inverting the output Q8 in the inverter 107 is obtained by AND109.
The reset signal φG is obtained as a result of logically combining the outputs Q4 and Q7 by the EX-OR 105,
It is output from the buffer 110.
The output Q8 is used as it is as the sensor drive signal φR and is output from the buffer 112.
As the sensor drive signal φS, a signal obtained by inverting the output Q8 by the inverter 107 is used and is output from the buffer 113.
Therefore, the reset signal having the first period in which the feedback amplifier 41 is activated for a predetermined period before the timing when the first sensor signal φR transits from the low level to the high level and the second sensor signal φS transits from the high level to the low level. φG, a reset signal φG having a second period in which the first sensor signal φR is at a high level and a second sensor signal φS is at a low level, and the feedback amplifier 41 is inactive for a predetermined period, and a first sensor signal φR. Is from a high level to a low level, and the reset signal φG has a third period in which the feedback amplifier 41 is activated only during a predetermined period before the timing when the second sensor signal φS transits from a low level to a high level, and the first sensor signal φR is a low level. , The feedback amplifier 41 is turned on only during a predetermined period when the second sensor signal φS is high level. A reset signal φG having a fourth period for deactivating is generated, and a reset signal φG that repeats these first, second, third, and fourth periods in a constant cycle is supplied to the feedback control switch (switching transistor 42). Supplied. By using these signal timings, the feedback amplifier 41 can add the capacitance values of the sensor capacitance Cs and the reference capacitance Cr as described above.
The present invention can also have the following configurations.
That is, referring to FIG. 3 showing the block diagram of the second embodiment, the difference from the first embodiment is that the gain amplifier 8 is inserted before the sample and hold units 5 and 6. is there. Since the other constituent elements are the same as those in the first embodiment, the description thereof will be omitted here. With this configuration, it is possible to obtain a gain according to the application.
That is, with reference to the reference voltage Vr of the output SCOUT of the switched capacitor section 4 in FIG. 1C, a voltage lower than the voltage Vr and a voltage higher than the voltage Vr are amplified to predetermined voltage levels, and the respective levels are increased. Since it is held by the sample and hold units 5 and 6 and is output via the differential amplifier unit 7, even if the gain amplifier 8 is inserted, the offset and temperature drift of the gain amplifier 8 are removed as in the first embodiment. can do.
Further, referring to FIG. 5 showing a block diagram of the third embodiment, the difference from the second embodiment is that a high pass filter (HPF) is provided between the gain amplifier 8 and the sample and hold units 5 and 6. ) 9 is inserted. Since the other constituent elements are the same as those in the first embodiment, the description thereof will be omitted here. With this configuration, the voltage of the output SCOUT of the switched capacitor unit 4 is amplified to a predetermined voltage level, and the HPF 9 allows only frequencies higher than the predetermined cutoff wave number to pass through, and then the level is sampled and held. Since the values are held in and and output through the differential amplifier 7, the gain amplifier 8 and the HPF 9 can be inserted to obtain a gain suitable for the application as in the second embodiment. It also becomes possible to remove offset, temperature drift and low frequency noise.
Similarly, by inserting a low-pass filter or a band-pass filter instead of the HPF 9 depending on the application, it is possible to remove high-frequency band noise or noise in both the high-frequency band and the low-frequency band, and to remove offset and temperature drift. Of course it is possible.
According to the capacitance change detection circuit and the detection method of the capacitance type sensor of the present invention described above, a predetermined sensor regards a physical phenomenon to be detected as a variation of the capacitance value of the electrostatic capacitance, and the difference in the capacitance value. Is converted into an electric signal by the switched capacitor unit, and the signal is sampled by the first and second sample and hold units having output signals having a mutual phase difference of 90 degrees, and then the difference between the respective sampling results is obtained. Since it has the detection means adapted to obtain a desired electric signal, it is possible to remove the influence of the offset voltage and the temperature drift of the feedback amplifier which constitutes the capacitance change detection circuit and the switching transistor for feedback control thereof, so that the ambient temperature can be eliminated. The capacitance change detection circuit of the highly reliable capacitive sensor that detects the capacitance difference extremely stably without being affected by It can be provided.
FIG. 1A is a block diagram of a capacitance change detection circuit of a capacitance type sensor according to a first embodiment of the present invention. (B) is a circuit diagram of a switched capacitor unit used in the first embodiment. (C) A timing chart for explaining the operation of the first embodiment.
FIG. 2 is a circuit diagram showing an example of a logic unit used in the first embodiment.
FIG. 3 is a block diagram showing a second embodiment.
FIG. 4 is a block diagram showing a third embodiment.
FIG. 5A is a block diagram showing an example of a conventional capacitance change detection circuit. (B) is a timing chart for explaining the operation.
1 Logic part 2 Sensor drive part 3 Sensor part 4 Switched capacitor part 5,6 Sample hold part 7 Differential amplification part 8 Gain amplification part 9 HPF 31 Sensor capacitance element 32 Reference capacitance element 41 Feedback amplifier 42 Switching transistor (feedback control switch) 43 feedback capacitance element 101 clock oscillator (OSC) 102, 103 counter 104 shift register 105, 106 EX-OR 107 inverter 108, 109 AND 110-114 buffer
1. A capacitance change detection circuit of a capacitance type sensor, wherein a predetermined sensor regards a physical phenomenon to be detected as a variation in capacitance value of an electrostatic capacitance, and a difference in the capacitance value is converted into an electric signal by a switched capacitor section. , Mutual phase difference 9
The first and second sample and hold units having the output signal of 0 degree sample the output signals of the switched capacitor unit, and then obtain the electric signal based on the difference between the sampling results. A capacitance change detection circuit of a capacitance type sensor having a detection means.
2. The detection means includes a first sample-hold section for sampling and outputting an output signal of one level of the switched capacitor section in response to a first sampling control signal, and another level of the switched capacitor section. A second sample-hold section for sampling and outputting the output signal in response to the second sampling control signal, and holding outputs of the first and second sample-hold sections are respectively supplied to the differential amplifier section, The capacitance change detection circuit of the capacitance type sensor according to claim 1, wherein the electric signal is generated by being differentially amplified.
3. The sensor capacitor element, wherein the switched capacitor section is driven by a first sensor drive signal and accumulates the change capacitance of the detection target, and the switch capacitor section is driven by a second sensor drive signal, and a capacitance value of the sensor capacitor element. And a reference capacitance element serving as a reference capacitance for taking the difference between the reference capacitance element and one of the sensor capacitance element and one end of the reference capacitance element are commonly connected to one input terminal, and a feedback capacitance element and a feedback control switch from the output terminal. Are connected in parallel and the other input terminal is connected to a predetermined reference potential, and the first sensor drive signal changes from low level to high level, and the second sensor drive signal A first reset period in which the feedback amplifier is activated only for a predetermined period before the timing of transition from a high level to a low level, A second reset period in which the feedback amplifier is inactive for a predetermined period in which the first sensor drive signal is at the high level and the second sensor drive signal is at the low level, and the first sensor drive signal changes from the high level to the low level. A third reset period in which the feedback amplifier is activated for a predetermined period immediately before the timing when the second sensor drive signal transits from the low level to the high level, and the first sensor drive signal is at the low level, and the second sensor drive is performed. A reset signal is supplied to the feedback control switch to repeat a fourth reset period in which the feedback amplifier is inactive for a predetermined period of a high level with a predetermined period, and the feedback amplifier switches the sensor capacitance to the sensor capacitance. Characterized in that the capacitance values of the element and the reference capacitance element are added. Capacitance change detection circuit of the capacitance type sensor according to claim 1, wherein.
4. A gain amplifying unit for amplifying an output of the switched capacitor unit, wherein the signals of the one level and the other level amplified to a predetermined level by the amplifying unit are the first and the second levels. 2. The capacitance change detection circuit for a capacitance type sensor according to claim 1, wherein the capacitance change detection circuit is supplied to each of the sample and hold sections.
5. A high-pass filter for removing low-frequency band noise, wherein the one-level signal and the other-level signal of the gain amplifier output from which low-frequency band noise is removed by using the high-pass filter are The capacitance change detection circuit for a capacitance type sensor according to claim 4, wherein the capacitance change detection circuit is supplied to each of the first and second sample and hold units.
6. A capacitance change detecting method for a capacitance type sensor, wherein a predetermined sensor regards a physical phenomenon to be detected as a change in capacitance value of capacitance, and the difference in capacitance value is converted into an electric signal by a switched capacitor section. , Mutual phase difference 9
The first and second sample-and-hold sections having an output signal of 0 degree sample the output signals of the switched capacitor section, respectively, and then the detection means obtains the electric signal based on the difference between the sampling results. Thus, the switched capacitor unit is driven by the first sensor drive signal and the capacitance value of the sensor capacitance element that accumulates the changed capacitance of the detection target, and the capacitance value of the sensor capacitance element that is driven by the second sensor drive signal. When the feedback amplifying means adds the capacitance value of the reference capacitance element serving as a reference capacitance for obtaining the difference from the value, and the feedback amplification means adds the capacitance values of the sensor capacitance element and the reference capacitance element; The first sensor drive signal transits from low level to high level, and the second sensor drive signal transits from high level to low level. A first reset period to activate the feedback amplifier means for a predetermined time before the timing,
A second reset period in which the feedback amplifying means is inactive for a predetermined time when the first sensor drive signal is at a high level and the second sensor drive signal is at a low level, and the first sensor drive signal is at a high level. From a low level to a low level, a third reset period in which the feedback amplifying means is activated for a predetermined time before the timing at which the second sensor drive signal transits from a low level to a high level, and the first sensor drive signal is low level, the second reset period. Supplying a reset signal to the feedback control switch of the feedback amplification means, which repeats a fourth reset period for inactivating the feedback amplification means for a predetermined time when the sensor drive signal is at a high level and a predetermined predetermined cycle. The capacitance change of the capacitance type sensor characterized in that the addition is executed by Way out.
JP6292859A 1994-11-28 1994-11-28 Capacitance sensor capacitance change detection circuit and detection method thereof Expired - Lifetime JP2561040B2 (en)
JP6292859A JP2561040B2 (en) 1994-11-28 1994-11-28 Capacitance sensor capacitance change detection circuit and detection method thereof
DE1995600956 DE69500956D1 (en) 1994-11-28 1995-11-28 Circuit arrangement for signal acquisition in a capacitive differential sensor
US08/563,486 US5633594A (en) 1994-11-28 1995-11-28 Differential type capacitive sensor system
EP19950118718 EP0715153B1 (en) 1994-11-28 1995-11-28 Differential type capacitive sensor system
DE1995600956 DE69500956T2 (en) 1994-11-28 1995-11-28 Circuit arrangement for signal acquisition in a capacitive differential sensor
JPH08145717A JPH08145717A (en) 1996-06-07
JP2561040B2 true JP2561040B2 (en) 1996-12-04
ID=17787301
JP6292859A Expired - Lifetime JP2561040B2 (en) 1994-11-28 1994-11-28 Capacitance sensor capacitance change detection circuit and detection method thereof
US (1) US5633594A (en)
EP (1) EP0715153B1 (en)
JP (1) JP2561040B2 (en)
DE (2) DE69500956T2 (en)
US10288467B2 (en) 2015-01-13 2019-05-14 Sumitomo Riko Company Limited Capacitance measurement device, capacitance-type sheet-shaped sensor apparatus, and capacitance-type liquid-level detector apparatus
JPH1026532A (en) * 1996-07-12 1998-01-27 Mitsubishi Electric Corp Semiconductor angular-velocity detecting device
JP3262013B2 (en) * 1997-02-24 2002-03-04 三菱電機株式会社 Capacitive sensor interface circuit
US5986497A (en) * 1997-05-16 1999-11-16 Mitsubishi Denki Kabushiki Kaisha Interface circuit for capacitive sensor
TW526327B (en) * 1998-02-19 2003-04-01 Sumitomo Metal Ind Detection apparatus and method of physical variable
US7635984B2 (en) * 1999-07-12 2009-12-22 Tk Holdings Inc. Electric field sensor and vehicle safety system
DE10001129A1 (en) * 2000-01-13 2001-07-26 Infineon Technologies Ag Circuit for measuring capacitances of structures in an IC enables voltage-dependent, differential capacitance measurement - has test and reference structures connected to junctions of series transistors in parallel circuits connected between poles of controllable voltage supply
JP4352562B2 (en) * 2000-03-02 2009-10-28 株式会社デンソー Signal processing device
DE10035192C1 (en) * 2000-07-20 2001-10-11 Carl Mahr Holding Gmbh Capacitive displacement measuring system for length measurement, has capacitive sensor provided by differential capacitor with two partial capacitors supplied with phase opposed control signals
JP4564258B2 (en) * 2001-09-19 2010-10-20 マイクロ−エプシロン・メステヒニク・ゲーエムベーハー・ウント・コンパニー・カー・ゲーＭｉｃｒｏ−Ｅｐｓｉｌｏｎ Ｍｅｓｓｔｅｃｈｎｉｋ Ｇｅｓｅｌｌｓｃｈａｆｔ Ｍｉｔ Ｂｅｓｃｈｒａｎｋｔｅｒ Ｈａｆｔｕｎｇ ＆ Ｃｏｍｐａｇｎｉｅ Ｋｏｍｍａｎｄｉｔｇｅｓｅｌｌｓｃｈａｆｔ Demodulator circuit
EP1329732A1 (en) * 2002-01-18 2003-07-23 Agilent Technologies, Inc. (a Delaware corporation) Determining cable attenuation and loss of signal threshold
JP2004279261A (en) 2003-03-17 2004-10-07 Denso Corp Physical quantity detector
JP4036798B2 (en) * 2003-07-29 2008-01-23 アルプス電気株式会社 Capacitance detection circuit, detection method, and fingerprint sensor
JP4440603B2 (en) 2003-11-06 2010-03-24 アルプス電気株式会社 Capacitance detection circuit, detection method, and fingerprint sensor using the same
JP2005140657A (en) * 2003-11-07 2005-06-02 Denso Corp Capacity change detecting circuit for electrostatic capacity type sensor
JP4387773B2 (en) * 2003-11-25 2009-12-24 アルプス電気株式会社 Capacitance detection circuit, detection method, and fingerprint sensor using the same
JP4364609B2 (en) 2003-11-25 2009-11-18 アルプス電気株式会社 Capacitance detection circuit and fingerprint sensor using the same
JP4447952B2 (en) * 2004-04-07 2010-04-07 アルプス電気株式会社 Charge detection circuit and fingerprint sensor using the same
JP2006229336A (en) * 2005-02-15 2006-08-31 Act Lsi:Kk Capacitive microphone
JP4315133B2 (en) * 2005-07-01 2009-08-19 セイコーエプソン株式会社 Solid-state imaging device
JP2007187509A (en) * 2006-01-12 2007-07-26 Denso Corp Physical quantity sensor of capacitance type
US7583088B2 (en) * 2007-01-26 2009-09-01 Freescale Semiconductor, Inc. System and method for reducing noise in sensors with capacitive pickup
US7743667B2 (en) * 2007-02-12 2010-06-29 Loadstar Sensors, Inc. Capacitive device and method with an enhanced measurement error correction capability
KR100974637B1 (en) * 2008-04-07 2010-08-06 서울대학교산학협력단 Capacitance detection apparatus and capacitive sensor having the same
WO2011092980A1 (en) * 2010-01-28 2011-08-04 株式会社村田製作所 Variable capacitance device
EP2781924B1 (en) * 2011-11-15 2016-06-01 Fuji Electric Co., Ltd. Capacitance detection circuit
EP2799891A1 (en) * 2013-05-03 2014-11-05 Sensirion AG Sensor circuit arrangement
TWI575461B (en) * 2015-02-13 2017-03-21 比亞迪股份有限公司 Fingerprint detection circuit, fingerprint detection method and electronic device
CN105447439B (en) * 2015-02-13 2017-05-03 比亚迪股份有限公司 Fingerprint detection circuit and electronic device
JP2017072468A (en) * 2015-10-07 2017-04-13 アルプス電気株式会社 Input device
US4831325A (en) * 1987-04-01 1989-05-16 General Signal Corporation Capacitance measuring circuit
US4814714A (en) * 1987-08-07 1989-03-21 Hazeltine Corporation Long time constant integrating circuit
JPH0672899B2 (en) * 1988-04-01 1994-09-14 株式会社日立製作所 Acceleration sensor
DE3915563C1 (en) * 1989-05-12 1990-10-25 Fraunhofer-Gesellschaft Zur Foerderung Der Angewandten Forschung Ev, 8000 Muenchen, De
DE4042336A1 (en) * 1990-02-12 1991-08-14 Fraunhofer Ges Forschung Integrated capacitive press sensor device - has capacitive sensor and capacitive reference element formed side-by-side on common substrate
1994-11-28 JP JP6292859A patent/JP2561040B2/en not_active Expired - Lifetime
1995-11-28 DE DE1995600956 patent/DE69500956T2/en not_active Expired - Lifetime
1995-11-28 EP EP19950118718 patent/EP0715153B1/en not_active Expired - Lifetime
1995-11-28 US US08/563,486 patent/US5633594A/en not_active Expired - Lifetime
1995-11-28 DE DE1995600956 patent/DE69500956D1/en not_active Expired - Lifetime
JPH08145717A (en) 1996-06-07
US5633594A (en) 1997-05-27
DE69500956D1 (en) 1997-12-04
EP0715153A1 (en) 1996-06-05
EP0715153B1 (en) 1997-10-29
DE69500956T2 (en) 1998-05-28
CN104679372B (en) 2019-08-16 Capacitive sensing interface for proximity test
KR100363287B1 (en) 2002-12-05 Method for determining very low capacitance and the use thereof
US8970227B2 (en) 2015-03-03 Circuit for capacitive touch applications
US20130300690A1 (en) 2013-11-14 Control circuit of touch screen and noise removing method
JP3125675B2 (en) 2001-01-22 Capacitive sensor interface circuit
DE10059775C2 (en) 2003-11-27 Method and device for processing analog output signals from capacitive sensors
US6700110B2 (en) 2004-03-02 Optical detector device
US8860437B2 (en) 2014-10-14 Readout system for MEMS-based capacitive accelerometers and strain sensors, and method for reading
TWI402513B (en) 2013-07-21 Capacitance evaluation circuit
DE19701899C2 (en) 2001-01-25 Circuit arrangement and method for detecting the capacitance or a change in capacitance of a capacitive circuit or component
EP1793497B1 (en) 2011-04-27 Device and method for reading a capacitive sensor, in particular of a micro-electromechanical type
US4893088A (en) 1990-01-09 Transimpedance focal plane processor
TWI472165B (en) 2015-02-01 Integration and analog to digital conversion circuit with common capacitors and operating method thereof
US6803802B2 (en) 2004-10-12 Switched-capacitor integrator
EP1779521B1 (en) 2018-03-28 Sigma-delta modulator
1996-07-31 A01 Written decision to grant a patent or to grant a registration (utility model)
2005-05-10 S111 Request for change of ownership or part of ownership
2005-05-18 R350 Written notification of registration of transfer
2005-06-09 RD02 Notification of acceptance of power of attorney
2014-11-28 EXPY Cancellation because of completion of term