Patent Publication Number: US-11652537-B2

Title: Interference canceling by fixed division of feeder link transmission band in multiple gateway HAPS system

Description:
TECHNICAL FIELD 
     The present invention relates to an interference canceling in a multi-feeder link of an aerial-floating type radio relay apparatus such as a HAPS suitable for constructing a three-dimensional network. 
     BACKGROUND ART 
     There is conventionally known a communication relay apparatus such as a high altitude platform station (HAPS) (also referred to as “high altitude pseudo satellite”) that can float and stay in an airspace (for example, see Patent Literature 1). A communication line in this aerial-floating type communication relay apparatus is configured with a feeder link between the communication relay apparatus and a gateway (GW) station on a mobile communication network side, and a service link between the communication relay apparatus and a terminal apparatus. 
     CITATION LIST 
     Patent Literature 
     
         
         Patent Literature 1: U.S. Patent Application Publication No. 2016/0046387. 
       
    
     SUMMARY OF INVENTION 
     Technical Problem 
     Since a communication capacity of the service link of the aerial-floating type communication relay apparatus (hereinafter referred to as “upper-air relay apparatus”) depends on a communication capacity of a feeder link which is a relay frequency, effective use of feeder link frequencies is essential. Therefore, a method is conceivable in which plural GW stations on the ground are installed at locations separated from each other to form a multi-feeder link that transmits and receives different feeder link signals on the same frequency from each GW station. However, unlike the fixed station, the upper-air relay apparatus flies around in a predetermined airspace, so that a dynamic interference may occur in the multi-feeder link of the same frequency between the upper-air relay apparatus and the plural GW stations. 
     Solution to Problem 
     A system according to an aspect of the present invention is a system comprising an aerial-staying type communication relay apparatus including a relay communication station that relays a radio communication of a terminal apparatus. The system comprises plural gateway stations that are time-synchronized with each other and transmit and receive relay signals different from each other on a same frequency in feeder links between the relay communication station of the aerial-staying type communication relay apparatus and the plural gateway stations. The relay communication station comprises a feeder-link communication section that transmits and receives relay signals different from each other on the same frequency in the feeder links to and from the plural gateway stations, and an interference suppression section that suppresses an interference between plural feeder links formed with the plural gateway stations. Each of the plural gateway stations transmits a pilot signal, and the feeder-link communication section receives the pilot signals respectively transmitted from the plural gateway stations, and separates each of the received plural pilot signals with a filter. The interference suppression section divides a transmission signal band of the feeder link into plural divided frequency bands, and estimates plural propagation path responses respectively between the plural gateway stations and an antenna for feeder link of the communication relay apparatus with respect to each of the plural divided frequency bands, by setting a center frequency of each of the plural divided frequency bands as an estimation frequency, based on a reception result of the pilot signals respectively received from the plural gateway stations and separated from each other. The interference suppression section calculates, for each of the divided frequency bands with respect to each of the plural gateway stations, a weight for suppressing an interference signal that causes an interference by a transmission signal transmitted from the gateway station and received with a directional beam corresponding to another gateway station, based on the plural propagation path responses. The interference suppression section subtracts, for each of the divided frequency bands with respect to each of the plural gateway stations, a reception signal received with a directional beam corresponding to the other gateway station multiplied by the weight corresponding to the other gateway station from the reception signal received by the directional beam corresponding to the other gateway station. 
     A relay communication station according to another aspect of the present invention is a relay communication station that is incorporated in an aerial-staying type communication relay apparatus and relays a radio communication of a terminal apparatus. The relay communication station comprises a feeder-link communication section that transmits and receives relay signals different from each other on a same frequency in feeder links between the feeder-link communication section and plural gateway stations that are time-synchronized with each other, and an interference suppression section that suppresses interferences between plural feeder links formed with the plural gateway stations and the interference suppression section. The feeder-link communication section receives pilot signals respectively transmitted from the plural gateway stations, and separates each of the received plural pilot signals with a filter. The interference suppression section divides a transmission signal band of the feeder link into plural divided frequency bands, and estimates plural propagation path responses respectively between the plural gateway stations and an antenna for feeder link of the communication relay apparatus with respect to each of the plural divided frequency bands, by setting a center frequency of each of the plural divided frequency bands as an estimation frequency, based on a reception result of the pilot signals respectively received from the plural gateway stations and separated from each other. The interference suppression section calculates, for each of the divided frequency bands with respect to each of the plural gateway stations, a weight for suppressing an interference signal that causes an interference by a transmission signal transmitted from the gateway station and received with a directional beam corresponding to another gateway station, based on the plural propagation path responses. The interference suppression section subtracts, for each of the divided frequency bands with respect to each of the plural gateway stations, a reception signal received with the directional beam corresponding to the other gateway station and multiplied by the weight corresponding to the other gateway station, from the reception signal received by the directional beam corresponding to the other gateway station. 
     An aerial-staying type communication relay apparatus according to yet another aspect of the present invention comprises the foregoing relay communication station. 
     An interference suppression method according to yet another aspect of the present invention is a feeder-link interference suppression method in a relay communication station that is incorporated in an aerial-staying type communication relay apparatus and relays a radio communication of a terminal apparatus. The interference suppression method includes receiving pilot signals respectively transmitted from plural gateway stations time-synchronized with each other, and separating each of the received plural pilot signals with a filter. Further, the interference suppression method includes dividing a transmission signal band of the feeder link into plural divided frequency bands, and estimating plural propagation path responses respectively between the plural gateway stations and an antenna for feeder link of the communication relay apparatus with respect to each of the plural divided frequency bands, by setting a center frequency of each of the plural divided frequency bands as an estimation frequency, based on a reception result of the pilot signals respectively received from the plural gateway stations and separated from each other, calculating, for each of the divided frequency bands with respect to each of the plural gateway stations, a weight for suppressing an interference signal that causes an interference by a transmission signal transmitted from the gateway station and received with a directional beam corresponding to another gateway station, based on the plural propagation path responses, and subtracting, for each of the divided frequency bands with respect to each of the plural gateway stations, a reception signal received with the directional beam corresponding to the other gateway station and multiplied by the weight corresponding to the other gateway station, from the reception signal received by the directional beam corresponding to the other gateway station. 
     A program according to yet another aspect of the present invention is a program executed by a computer or a processor installed in a relay communication station that is incorporated in an aerial-staying type communication relay apparatus and relays a radio communication of a terminal apparatus. The program includes a program code for transmitting and receiving relay signals different from each other on a same frequency in feeder links between the relay communication station and plural gateway stations that are time-synchronized with each other, a program code for receiving pilot signals respectively transmitted from the plural gateway stations, a program code for separating each of the received plural pilot signals with a filter. Further, the program includes a program code for dividing a transmission signal band of the feeder link into plural divided frequency bands, and estimating plural propagation path responses respectively between the plural gateway stations and an antenna for feeder link of the communication relay apparatus with respect to each of the plural divided frequency bands, by setting a center frequency of each of the plural divided frequency bands as an estimation frequency, based on a reception result of the pilot signals respectively received from the plural gateway stations and separated from each other, a program code for calculating, for each of the divided frequency bands with respect to each of the plural gateway stations, a weight for suppressing an interference signal that causes an interference by a transmission signal transmitted from the gateway station and received with a directional beam corresponding to another gateway station, based on the plural propagation path responses, and a program code for subtracting, for each of the divided frequency bands with respect to each of the plural gateway stations, a reception signal received with the directional beam corresponding to the other gateway station and multiplied by the weight corresponding to the other gateway station, from the reception signal received by the directional beam corresponding to the other gateway station. 
     In the foregoing system, the foregoing relay communication station, the foregoing aerial-staying type communication relay apparatus, the foregoing interference suppression method and the foregoing program, the plural divided frequency bands may be frequency bands defined by equally dividing the transmission signal band of the feeder link, or may be defined by unequally dividing the transmission signal band of the feeder link according to a distribution of the interference signals in the transmission signal band of the feeder link. 
     In the foregoing system, the foregoing relay communication station, the foregoing aerial-staying type communication relay apparatus, the foregoing interference suppression method and the foregoing program, the pilot signals may be plural, and the plural pilot signals may be distributed and transmitted in plural guard bands located on both sides of the transmission signal band of the feeder link. 
     In the foregoing system, the foregoing relay communication station, the foregoing aerial-staying type communication relay apparatus, the foregoing interference suppression method and the foregoing program, each of the plural weights may be calculated by the ZF (Zero-Forcing) method or the MMSE (Minimum Mean Square Error) method using matrix of the propagation path response. 
     In the foregoing system, the foregoing interference suppression method and the foregoing program, each of the plural gateway stations may comprise an antenna control section that controls an antenna for feeder link so as to track the aerial-staying type communication relay apparatus. 
     In the foregoing system, the foregoing aerial-staying type communication relay apparatus, the foregoing interference suppression method and the foregoing program, the aerial-staying type communication relay apparatus may comprise an antenna for feeder link having plural directional beams corresponding to each of the plural gateway stations, and an antenna control section for controlling the antenna for feeder link so that each of the plural beams directs toward a corresponding gateway station. 
     Advantageous Effects of Invention 
     According to the present invention, it is possible to suppress an interference in a multi-feeder link of a same frequency between an aerial-floating type communication relay apparatus and plural gateway stations. 
    
    
     
       BRIEF DESCRIPTION OF DRAWINGS 
         FIG.  1    is an illustration showing an example of a HAPS cell configuration in a communication system according to an embodiment of the present invention. 
         FIG.  2 A  is a side view showing an example of a schematic configuration of plural GW systems according to the embodiment. 
         FIG.  2 B  is a top view illustration of a relationship between plural antennas for feeder link of a HAPS and plural GW stations. 
         FIG.  3    is an illustration showing an example of state in which GW antennas of plural GW stations are tracking a HAPS according to the embodiment. 
         FIG.  4    is an illustration showing an example of directional beams of plural FL antennas of a HAPS according to the embodiment. 
         FIG.  5    is an illustration showing an example of a directional beam control of FL antennas in a HAPS according to the embodiment. 
         FIG.  6    is an illustration showing another example of a directional beam control of FL antennas in a HAPS according to the embodiment. 
         FIG.  7    is an illustration showing yet another example of a directional beam control of FL antennas in a HAPS according to the embodiment. 
         FIG.  8    is an illustration of an example of an interference between GW stations (between feeder links) in plural GW systems. 
         FIG.  9    is an illustration showing an example of a MIMO interference canceller applied by obtaining the weight W by an approximate expression. 
         FIG.  10    is an illustration showing an example of a schematic configuration of an interference canceller section mounted on a HAPS. 
         FIG.  11    is an illustration showing an example of a MIMO interference canceller applied by obtaining the weight W by the ZF method. 
         FIG.  12    is an illustration showing a reference example of a transmission signal band of a feeder link in the plural GW systems. 
         FIG.  13    is a graph showing an example of a computer simulation result that evaluates an interference reduction effect when the weights are obtained at pilot frequencies different from each other according to the reference example. 
         FIG.  14    is a graph showing an example of a computer simulation result of SINR characteristics of an entire transmission signal band of a feeder link in case that an airframe of HAPS is rotated. 
         FIG.  15    is an illustration showing a reference example of frequencies of respective pilot signals in case that each of plural GW stations transmits a single pilot signal. 
         FIG.  16    is an illustration showing an example of a derivation model of a propagation path response of a feeder link using the pilot signal in  FIG.  15   . 
         FIG.  17    is an illustration showing a reference example of a frequency arrangement of respective pilot signals in case that each of plural GW stations transmits plural pilot signals. 
         FIG.  18    is an illustration showing an example of a derivation model of a propagation path response of a feeder link using the pilot signals in  FIG.  17   . 
         FIG.  19    is an illustration showing another reference example of an arrangement of pilot frequencies in case that each of plural GW stations transmits plural pilot signals. 
         FIG.  20    is an illustration showing yet another reference example of an arrangement of pilot frequencies in case that each of plural GW stations transmits plural pilot signals. 
         FIG.  21    is a graph showing an example of an interference reduction effect when the weight is obtained based on a propagation path response estimated by setting each of a center frequency and a frequency at a low-frequency side end of the feeder-link transmitting signal band FB as an estimation frequency. 
         FIG.  22    is an illustration showing an example of a frequency division and an interference quantity reduction of the transmission signal band FB of the feeder link in the feeder-link interference suppression process according to the present embodiment. 
         FIG.  23    is a graph showing an example of a relationship between the number of divisions of the transmission signal band FB and the SINR when receiving the feeder link of HAPS in the feeder-link interference suppression process according to the present embodiment. 
         FIG.  24    is an illustration showing another example of a frequency division and an interference quantity reduction of the transmission signal band FB of the feeder link in the feeder-link interference suppression process according to the present embodiment. 
         FIG.  25    is an illustration showing an example of a main configuration of a relay communication station of HAPS according to the present embodiment. 
     
    
    
     DESCRIPTION OF EMBODIMENTS 
     Hereinafter, embodiments of the present invention are described with reference to the drawings. 
       FIG.  1    is an illustration showing an example of a cell configuration of HAPS  20  in a communication system according to an embodiment of the present invention. The communication system according to the present embodiment is suitable for realizing a three-dimensional network of fifth-generation mobile communication that supports simultaneous connection to a large number of terminal apparatuses, and low delay, etc. 
     As shown in  FIG.  1   , the communication system is provided with High-Altitude Platform Stations (HAPS) (also called “high altitude pseudo satellite” or “stratified platform”)  20  as plural aerial-floating type communication relay apparatuses (radio relay apparatuses). The HAPS  20  is located in an airspace at a predetermined altitude, and forms three-dimensional cell (three-dimensional area) in a cell-formation target airspace at a predetermined altitude. The HAPS  20  is an airship as a floating object that is controlled by autonomous control or external control so as to float or fly and be located in an airspace (floating airspace) with high altitude of 100 [km] or less from the ground level or the sea level, and a relay communication station  21  is mounted on the airship. 
     The airspace in which the HAPS  20  is located is, for example, a stratospheric airspace with altitude greater than 11 [km] and less than 50 [km] on the ground (or on the water such as the sea or lake). The airspace may be an airspace in an altitude of 15 [km] or more and 25 [km] or less where weather conditions are relatively stable, and may be an airspace with altitude of about 20 [km] in particular. 
     The cell-formation target airspace, which is a target airspace for forming a three-dimensional cell with one or two or more HAPSs according to the communication system in the present embodiment, is an airspace in a predetermined altitude range (for example, altitude range of 50 [m] or more and 1000 [m] or less) located between the airspace where the HAPS  20  is located and a cell-formation spatial area near the ground level covered by a base station (for example, LTE eNodeB) such as a conventional macro-cell base station. 
     It is noted that, the cell-formation target airspace where the three-dimensional cell in the present embodiment is formed may be an airspace over the sea, a river or a lake. Further, the three-dimensional cell formed by the HAPS  20  may be formed so as to reach the ground level or the sea level so that it can communicate with a terminal apparatus  61  located on the ground or on the sea. 
     The relay communication stations of the HAPS  20  respectively form plural beams for wirelessly communicating with the terminal apparatus  61  that is a mobile station, toward the ground by an antenna for service link (hereinafter referred to as “SL antenna”)  215 . The terminal apparatus  61  may be a communication terminal module incorporated in a drone that is an aircraft such as a small helicopter capable of remotely steering, or may be a user apparatus used by a user in an airplane. An area through which the beam passes in the cell-formation target airspace is a three-dimensional cell. The plural beams adjacent to each other in the cell-formation target airspace may be partially overlapped with each other. 
     Each of the relay communication stations  21  of the HAPS  20  is, for example, a base station that wirelessly communicates with a gateway station (also referred to as a “feeder station”)  70  as a relay station connected to a core network on the ground (or on the sea) side, or a slave repeater that wirelessly communicates with the feeder station (master repeater)  70  as a relay station connected to a base station on the ground (or on the sea) side. 
     The relay communication station  21  of the HAPS  20  is connected to a core network of a mobile communication network  80  via the feeder station  70 , which is installed on the ground or on the sea, capable of radio communication by an antenna for feeder link (hereinafter referred to as “FL antenna”)  211 . A communication of feeder link between the HAPS  20  and the feeder station  70  may be performed by a radio communication using a radio wave such as a microwave, or may be performed by an optical communication using a laser light or the like. 
     Each of the HAPS  20  may autonomously control its own floating movement (flight) and a process in the relay communication station  21  by executing a control program with a control section including a computer or the like incorporated inside of the HAPS. For example, each of the HAPS  20  may acquire its own current position information (for example, GPS position information), position control information (for example, flight schedule information) stored in advance, position information on another HAPS located in a peripheral space or the like, and may autonomously control floating movement (flight) and process in the relay communication station  21  based on these pieces of information. 
     Further, the floating movement (flight) of each of the HAPS  20  and the process in the relay communication station  21  may be controlled by a management apparatus (also referred to as a “remote control apparatus”) as a management apparatus provided in a communication center or the like of the mobile communication network. The management apparatus can be configured with, for example, a computer apparatus such as a PC, a server, or the like. In this case, the HAPS  20  may incorporate a communication terminal apparatus for control (for example, mobile communication module) so that it can receive control information from the management apparatus and transmit various pieces of information such as monitoring information to the management apparatus, and may be assigned terminal identification information (for example, IP address, phone number, etc.) so that it can be identified from the management apparatus. The MAC address of the communication interface may be used to identify the communication terminal apparatus for control. 
     Moreover, each of the HAPS  20  may transmit information regarding the floating movement (flight) of the own HAPS or a surrounding HAPS and/or the process at the relay communication station  21 , and monitoring information such as information on statuses of the HAPS  20  and observation data acquired by various kinds of sensors, to a predetermined destination such as the management apparatus. The control information may include information on target flight route of the HAPS. The monitoring information may include at least one of information on current positions, flight-route history information, velocity relative to the air, velocity relative to the ground and propulsion direction of the HAPS  20 , wind velocity and wind direction around the HAPS  20 , and atmospheric pressure and temperature around the HAPS  20 . 
     Duplex methods of uplink and downlink for radio communication with the relay communication station  21  and the terminal apparatus  61  are not limited to specific methods, and may be, for example, a time division duplex method (Time Division Duplex: TDD) or a frequency division duplex method (Frequency Division Duplex: FDD). An access method for radio communication with the relay communication station  21  and the terminal apparatus  61  is not limited to the specific method, but may be, for example, FDMA (Frequency Division Multiple Access) method, TDMA (Time Division Multiple Access) method, CDMA (Code Division Multiple Access) method, or OFDMA (Orthogonal Frequency Division Multiple Access). In the foregoing radio communication, a MIMO (Multi-Input and Multi-Output) technology may be used, which has functions of diversity/coding, transmission beam forming, spatial division multiplexing (SDM: Spatial Division Multiplexing), etc., and in which a transmission capacity per unit frequency can be increased by simultaneously using plural antennas for both of transmission and reception. The MIMO technology may be an SU-MIMO (Single-User MIMO) technology in which one base station transmits plural signals to one terminal apparatus on the same time/same frequency, and may be an MU-MIMO (Multi-User MIMO) technology in which one base station transmits signals to plural different communication terminal apparatuses on the same time/same frequency or plural different base stations transmit signals to one terminal apparatus on the same time/same frequency. 
     It is noted that, in the following embodiments, although it is illustrated and described regarding some cases in which a communication relay apparatus having the relay communication station  21  that wirelessly communicates with the terminal apparatus  61  is an unmanned airship type HAPS  20 , the communication relay apparatus may be a solar-plane type HAPS. Further, the following embodiments can be similarly applied to aerial-floating type communication relay apparatuses other than the HAPS. 
     A link between the HAPS  20  and a base station  90  via a gateway station (hereinafter abbreviated as “GW station”)  70  as a feeder station is referred to as a “feeder link”, and a link between the HAPS  10  and the terminal apparatus  61  is referred to as a “service link”. In particular, a spatial section between the HAPS  20  and the GW station  70  is referred to as a “radio section of feeder link”. Further, a downlink of a communication from the GW station  70  to the terminal apparatus  61  via the HAPS  20  is referred to as a “forward link”, and an uplink of a communication from the terminal apparatus  61  to the GW station  70  via the HAPS  20  is also referred to as a “reverse link”. 
     In  FIG.  1   , although the communication relay apparatus is the unmanned-airship type HAPS  20 , it may be a solar-plane type HAPS. Further, in the illustrated example, although the HAPS  20  is located in the stratosphere with an altitude of about 20 km, the HAPS  20  forms plural cells  200 C( 1 ) to  200 C( 7 ), and a diameter of a service area  20 A consisting of footprints  200 F( 1 ) to  200 F( 7 ) of the cells  200 C( 1 ) to  200 C( 7 ) of the plural cells (7 cells) configuration is 100 to 200 km, it is not limited to these examples. 
     In  FIG.  1   , a communication service that directly communicates with the terminal apparatus  61  on the ground (or on the water) using the HAPS  20  located in the stratosphere is very attractive as an expansion of service area and a communication means in the event of a disaster. The communication line of the HAPS  20  comprises a feeder link FL connecting the GW station  70  and the HAPS  20 , and a service link SL connecting the HAPS  20  and the terminal apparatus  61 . Since the communication capacity of the service link depends on the communication capacity of the feeder link which is the relay frequency, it is necessary to improve the frequency utilization efficiency of the feeder link. In particular, in case that the service link has a multi-cell configuration as shown in  FIG.  9   , the communication capacity of the feeder link tends to be insufficient, so that a frequency effective utilization technology for the feeder link is indispensable. However, in case that the HAPS  20  and the GW station  70  are configured one-to-one, it is difficult to improve the frequency utilization efficiency of the feeder link. 
     Therefore, in the present embodiment, a plural-gateway system (hereinafter also referred to as “plural-GW system”) is constructed, which is configured with plural GW stations that transmit and receive relay signals different from each other on a same frequency to and from the HAPS  20  in the feeder link, and performs a spatial-division multiplex communication in a multi-feeder link formed between one HAPS  20  and plural GW stations. In the plural-GW system, by eliminating interference between the plural feeder links, the frequency utilization efficiency can be improved depending on the number of GW stations to be installed. 
     It is noted that, in the following embodiments, although it is described regarding some cases in which the spatial-division multiplex communication between the HAPS  20  and the plural GW stations is performed only by a forward link of the feeder link, the spatial-division multiplex communication may be performed only by a reverse link of the feeder link, or may be performed by both of the forward link and the reverse link. 
       FIG.  2 A  is a side view showing an example of a schematic configuration of plural GW systems according to the embodiment, and  FIG.  2 B  is a top view illustration of a relationship between plural FL antennas  211 ( 1 ) to  211 ( 3 ) of the HAPS  20  and plural GW stations  70 ( 1 ) to  70 ( 3 ). In the illustrated example, each of the number of FL antennas (N) and the number of GW stations (N) is the same number ( 3  in the illustrated example), and the same number of FL antennas  211 ( 1 ) to  211 ( 3 ) and GW stations  70 ( 1 ) to  70 ( 3 ) are provided in a one-to-one correspondence with each other. The number of sets of the FL antenna  211  and the GW station  70  may be two sets, or may be four or more sets. Further, in the illustrated example, although the plural GW stations  70  are disposed so that distances from the HAPS  20  and intervals between the GW stations are equal to each other, at least one of the distances and the intervals may be different from each other. Each GW station  70  is disposed so that complex amplitudes received by each FL antenna  211  (also referred to as “HAPS station antenna”) of the HAPS  20  are uncorrelated. Further, the antennas for feeder link (hereinafter referred to as “GW antennas”)  71 ( 1 ) to  71 ( 3 ) of the GW stations  70 ( 1 ) to  70 ( 3 ) can transmit and receive radio signals with two kinds of polarized waves of vertically polarized waves (V) and horizontally polarized waves (H) which are orthogonal to each other. In the illustrated example, although the plural FL antennas  211 ( 1 ) to  211 ( 3 ) of the HAPS  20  are disposed so that distances from the center of the HAPS  20  and intervals between the FL antennas are equal to each other, at least one of the distances and the intervals may be different from each other between the FL antennas. For example, the distances and the intervals may be different from each other between the FL antennas. 
     As shown in  FIG.  3   , each of the plural GW stations  70 ( 1 ) to  70 ( 3 ) may include an antenna control section that controls the GW antennas  71 ( 1 ) to  71 ( 3 ) so as to track the HAPS  20  moving in an airspace. A HAPS  20 ′ with dashed lines in the figure indicates a position before the movement, and a HAPS  20  with solid lines in the figure indicates a position after the movement. By tracking the HAPS  20  by each of the GW antennas  71 ( 1 ) to  71 ( 3 ), even when using the GW antennas  71 ( 1 ) to  71 ( 3 ) with high directivity such as a parabolic antenna, it is capable of suppressing the deterioration of the communication quality of the feeder link due to the movement of the HAPS  20 . 
     As shown in  FIG.  4   , the plural FL antennas  211 ( 1 ) to  211 ( 3 ) of the HAPS  20  may include antenna directional beams (hereinafter referred to as “directional beams” or “beams”)  212 ( 1 ) to  212 ( 3 ) respectively corresponding to the GW stations  70 ( 1 ) to  70 ( 3 ), and the HAPS  20  may include an antenna control section that controls the FL antennas  211 ( 1 ) to  211 ( 3 ) so that the directional beams  212 ( 1 ) to  212 ( 3 ) of the plural FL antennas  211 ( 1 ) to  211 ( 3 ) is respectively directed in the direction of the corresponding GW stations  70 ( 1 ) to  70 ( 3 ). Each of the directional beams  212 ( 1 ) to  212 ( 3 ) of the FL antennas  211 ( 1 ) to  211 ( 3 ) is formed, for example, so as to face the GW station  70  closest to itself and not to provide interferences to other GW stations, that is, so that a ratio (F/B) of a gain of the main beam and a gain in the opposite direction becomes sufficiently large. As a result, even when the HAPS  20  moves or rotates, it is possible to suppress the deterioration of the communication quality of the feeder link due to the movement and rotation of the HAPS  20 . 
     As a control system of the directional beams  212 ( 1 ) to  212 ( 3 ) of the plural FL antennas  211 ( 1 ) to  211 ( 3 ) by the antenna control section of the HAPS  20 , it is capable of using various systems such as a gimbal system, an electric system (360-degrees beamforming control system), and an electric system (angle-limited beamforming control system+antenna switching). 
     For example, in the gimbal system in  FIG.  5   , in accordance with the rotation (turning) around the vertical axis (yawing axis, Z axis) of the HAPS  20 , the rotation drive of the whole of plural FL antennas  211 ( 1 ) to  211 ( 3 ) can be mechanically controlled around the foregoing axis. For example, in  FIG.  5   , when the HAPS  20  rotates about 45 degrees in the left direction of rotation (counterclockwise direction) Rb, the rotation of the whole of plural FL antennas  211 ( 1 ) to  211 ( 3 ) are mechanically driven in the right direction of rotation (clockwise direction) Ra opposite to the foregoing direction of rotation of the HAPS  20 . 
     Although the rotational drive control for angle adjustment of each of the FL antenna  211 ( 1 ) to  211 ( 3 ) may be performed with reference to information on a position and an orientation of the HAPS, the rotational drive control of respective FL antenna  211 ( 1 ) to  211 ( 3 ) may be performed with reference to reception level values of the FL antennas  211 ( 1 ) to  211 ( 3 ). For example, each FL antenna  211 ( 1 ) to  211 ( 3 ) is rotated in small steps, an angle for maximizing the reception level of each of the FL antenna  211 ( 1 ) to  211 ( 3 ) is found, and the rotational drive control of each of the FL antenna  211 ( 1 ) to  211 ( 3 ) is performed so as to face the angle. Herein, a threshold value may be set for each of the reception levels of each of the FL antenna  211 ( 1 ) to  211 ( 3 ), each of the FL antenna  211 ( 1 ) to  211 ( 3 ) may be rotated by a predetermined angle when the reception level falls below the foregoing threshold value, and the rotational drive control of the FL antenna  211 ( 1 ) to  211 ( 3 ) may be performed to the directional angle at which the reception level is maximized. The threshold value of the reception level may be obtained, for example, by an experiment in advance, and the predetermined angle may be, for example, 360 degrees/number of FL antennas (120 degrees in the illustrated example). Further, a monitoring beam for comparing the reception level from the GW stations other than the corresponding GW station may be generated from the FL antenna  211 ( 1 ) to  211 ( 3 ), a GW station having the maximum level may be selected, and the rotational drive of each of the FL antenna  211 ( 1 ) to  211 ( 3 ) may be controlled so that the directional beam is directed in the direction to the selected GW station. 
     It is noted that, although the angle adjustment in the horizontal direction of each of the FL antennas  211 ( 1 ) to  211 ( 3 ) is shown in  FIG.  5   , the angle adjustment in the vertical direction may be also performed in the same manner. 
     By the rotational drive control of the FL antennas  211 ( 1 ) to  211 ( 3 ), even if the HAPS  20  rotates, since the directional beams  212 ( 1 ) to  212 ( 3 ) of the FL antennas  211 ( 1 ) to  211 ( 3 ) are directed in the corresponding directions of the GW stations  70 ( 1 ) to  70 ( 3 ) respectively, the deterioration of the communication quality of the feeder link can be prevented. 
     In the electric system (360-degrees beamforming control system) in  FIG.  6   , a circular array antenna  213  in which plural antenna elements  213   a  are disposed along the circumferential shape is provided as a FL antenna. Based on information on a position and an attitude of the HAPS  20 , a weight applied to signals (amplitude, phase) transmitted and received via each of the plural antenna elements  213   a  is controlled. For example, the information on the position and the attitude of the HAPS  20  may be acquired based on an output of a GNSS Inertial Navigation System (GNSS/INS) that is a combination of a GNSS (Global Navigation Satellite System) system and an Inertial Measurement Unit (IMU) incorporated in the HAPS  20 . 
     Although the weight control of each antenna element  213   a  of the circular array antenna  213  may be performed with reference to the information on the position and the attitude of the HAPS, the weight control of each antenna element  213   a  may be performed so as to form a directional beam having the maximum reception level at a directional position corresponding to each GW station with reference to the reception level value of each antenna element  213   a  of the circular array antenna  213 . For example, a phase of each antenna element  213   a  of the circular array antenna  213  is changed in small steps, an angle for maximizing the reception level is found, and the weight control of each antenna element  213   a  is performed so that a beam is formed in the direction of the found angle. Further, a monitoring beam for comparing the reception level from the GW stations other than the corresponding GW station may be generated from the circular array antenna  213 , a GW station having the maximum level may be selected, and a beam may be formed in the direction to the selected GW station. 
     It is noted that, although the beam angle adjustment in the horizontal direction is shown in  FIG.  6   , the beam angle adjustment may be also performed in the same manner in the vertical direction. 
     By controlling the weight of each antenna element  213   a  of the circular array antenna  213 , the directional beams  212 ( 1 ) to  212 ( 3 ) respectively directed in the directions to the plural GW stations  70 ( 1 ) to  70 ( 3 ) are formed. As a result, even if the HAPS  20  rotates, since the directional beams  212 ( 1 ) to  212 ( 3 ) of the FL antennas  211 ( 1 ) to  211 ( 3 ) are directed in the corresponding directions to the GW stations  70 ( 1 ) to  70 ( 3 ) respectively, the deterioration of the communication quality of the feeder link can be prevented. 
     In the electric system (beamforming control system with limited angle+antenna switching) of  FIG.  7   , plural planar array antennas  214 ( 1 ) to  214 ( 3 ), in which plural antenna elements  214   a  of each array antenna are two-dimensionally disposed in a plane, are provided as a FL antenna. Based on information on the position and the attitude of the HAPS  20  acquired by GNSS/INS etc., a beamforming control is performed to control a weight applied to a signal (amplitude, phase) transmitted and received via each of the plural antenna elements  214   a  of the plural planar array antennas  214 ( 1 ) to  214 ( 3 ). 
     Although the control of the switching and the beamforming of the planar array antennas  214 ( 1 ) to  214 ( 3 ) may be performed with reference to the information on the position and the attitude of the HAPS, the antenna switching and beamforming may be controlled so that each of the planar array antennas  214 ( 1 ) to  214 ( 3 ) has the maximum reception level with reference to the reception level value of each planar array antenna  214 ( 1 ) to  214 ( 3 ). For example, each of the planar array antenna  214 ( 1 ) to  214 ( 3 ) is rotated in small steps, an angle for maximizing the reception level of respective planar array antenna  214 ( 1 ) to  214 ( 3 ) is found, and the rotational drive control of each antenna is performed so as to be directed to the found angle. Herein, a threshold value may be set for each of the reception levels of each of the planar array antenna  214 ( 1 ) to  214 ( 3 ), when the reception level falls below the foregoing threshold value, the planar array antennas  214 ( 1 ) to  214 ( 3 ) may be switched and each of the planar array antenna  214 ( 1 ) to  214 ( 3 ) may be rotated by a predetermined angle, and a beamforming may be performed to form a beam to the directional angle at which the reception level is maximized. The threshold value of the reception level may be obtained, for example, by an experiment in advance, and the predetermined angle may be, for example, 360 degrees/number of FL antennas (120 degrees in the illustrated example). Further, a monitoring beam for comparing the reception level from the GW stations other than the corresponding GW station may be generated from the planar array antenna  214 ( 1 ) to  214 ( 3 ), a GW station, for which each of the planar array antenna  214 ( 1 ) to  214 ( 3 ) has the maximum level, may be selected, and an antenna switching and a beamforming may be performed so as to form a beam in the direction to the selected GW station. 
     It is noted that, although the beam angle adjustment in the horizontal direction is shown in  FIG.  7   , the beam angle adjustment may be also performed in the same manner in the vertical direction. 
     By controlling the switching and the beamforming of the planar array antennas  214 ( 1 ) to  214 ( 3 ), the directional beams  212 ( 1 ) to  212 ( 3 ) respectively directed in the directions to the plural GW stations  70 ( 1 ) to  70 ( 3 ) are formed. Herein, for example, when the angle (θ in the figure) at which the directional beam  212 ( 1 ) is tilted with respect to the normal direction perpendicular to the plane of the planar array antenna  214 ( 1 ) becomes larger than the preset predetermined angle θth degrees, the FL antenna corresponding to the GW station  70 ( 1 ) is switched to the planar array antenna  214 ( 2 ). As a result, even if the HAPS  20  rotates, each of the directional beams  212 ( 1 ) to  212 ( 3 ) of the FL antennas  211 ( 1 ) to  211 ( 3 ) are directed in the directions to the corresponding GW stations  70 ( 1 ) to  70 ( 3 ), so that the deterioration of the communication quality of the feeder link can be prevented. 
     In the plural-GW system having the above-described configuration, interference between GW stations (between feeder links) may increase. For example, as shown in  FIG.  8   , while a desired signal (desired signal) S 1  transmitted from the GW station  70 ( 1 ) is received by the FL antenna  211 ( 1 ) of the HAPS  20 , signals transmitted from the other GW stations  70 ( 2 ) and  70 ( 3 ) are received by the FL antenna  211 ( 1 ) as interference signals I 2  and I 3 . Therefore, SINR characteristics of the feeder link may deteriorate. 
     Therefore, in the present embodiment, by applying a MIMO interference canceller supporting the line-of-sight environment (LOS: Line-Of-Sight) between the GW stations (between the feeder links) as shown below, and by reducing the interferences between the GW stations (between the feeder links), the SINR characteristics of the feeder link are improved. 
       FIG.  9    is an illustration showing an example of a MIMO interference canceller applied by obtaining the weight W by an approximate expression.  FIG.  10    is an illustration showing an example of a schematic configuration of an interference canceller section  220  mounted on the HAPS  20 . 
     The FL antenna  211 ( 1 ) of the HAPS  20  receives a desired signal S 1 (Y 11 ) transmitted from the GW station  70 ( 1 ), an interference signal I 2 (Y 12 ) transmitted from the GW station  70 ( 2 ), and an interference signal I 3 (Y 13 ) transmitted from the GW station  70 ( 3 ). The reception signal AN 1  is represented by the following equation (1).
 
 AN 1= S 1+ I 2+ I 3  (1)
 
     In the interference canceller section  220  of the HAPS  20 , by multiplying and subtracting the weights W 2  and W 3  corresponding to the signals S 2  and S 3  respectively received by the other FL antennas  211 ( 2 ) and  211 ( 3 ) as shown in the following equation (2), the desired signal S 1 (Y 11 ), in which the interference signals I 2  and I 3  are cancelled, can be output. Similarly, the interference signals from other GW stations can be canceled for the desired signals S 2 (Y 22 ) and S 3 (Y 33 ) transmitted from the GW stations  70 ( 2 ) and  70 ( 3 ).
 
 S 1= w 11· AN 1+ w 12· AN 2+ w 13· AN 3   (2)
 
       FIG.  11    is an illustration showing an example of a MIMO interference canceller applied by obtaining a weight W by the ZF (Zero-Forcing) method. For example, a signal transmitted from the GW station  70 ( 1 ) is not only received as the desired signal S 1 (Y 11 ) by the FL antenna  211 ( 1 ) of the HAPS  20 , but also received as interference signals I 1 (Y 12 ) and I 1 ′(Y 13 ) by the FL antennas  211 ( 2 ) and  211 ( 3 ). Further, a signal transmitted from the GW station  70 ( 2 ) is not only received as an interference signal I 2 (Y 21 ) by the FL antenna  211 ( 1 ), but also received as an interference signal I 2 ′(Y 23 ) by the FL antenna  211 ( 3 ). Moreover, a signal transmitted from the GW station  70 ( 3 ) is not only received as an interference signal I 3 (Y 31 ) by the FL antenna  211 ( 1 ), but also received as an interference signal I 3 ′(Y 32 ) by the FL antenna  211 ( 2 ). In the MIMO interference canceller in  FIG.  11   , considering these interference signals I 1 , I 1 ′, I 2 ′ and I 3 ′, the desired signal S 1 (Y 11 ) is output, for example, as shown in the following equation (3). As a result, the accuracy of interference suppression between the GW stations (between the feeder links) can be improved.
 
 S 1= w 11( Y 11+ Y 12+ Y 13)+ w 12( Y 21+ Y 22+ Y 23)+ w 13( Y 31+ Y 32+ Y 33)   (3)
 
     In order to calculate the weight W used for the MIMO interference canceller, it is necessary to grasp a propagation path response H between the FL antennas  211 ( 1 ) to  211 ( 3 ) of the HAPS  20 . In particular, in the plural GW systems in the present embodiment, since the airframe of the HAPS  20  moves relative to the GW stations  70 ( 1 ) to  70 ( 3 ), the propagation path response also changes in accordance with to the movement. 
     Therefore, in the present embodiment, a pilot signal is transmitted from each of the GW stations  70 ( 1 ) to  70 ( 3 ) in order to grasp the propagation path response. The frequency band of the pilot signal is a narrow band, and each pilot signal has a different transmission frequency from each other (orthogonal). The relay communication station  21  of the HAPS  20  estimates, for example, the propagation path response of the center frequency fsc (see fsc in  FIG.  12   ) of the transmission signal band FB of the feeder link based on the pilot signal received from each of the GW stations  70 ( 1 ) to  70 ( 3 ), and derives the weight W. 
     The larger the difference between the frequency for obtaining the weight W and the transmission signal band of the feeder link, the smaller the amount of interference cancellation. For example, in the plural-GW system in  FIG.  2 A  and  FIG.  2 B  described above, three GW stations  70 ( 1 ) to  70 ( 3 ) are installed at every 120°, and three FL antennas  211 ( 1 ) to  211 ( 3 ) of the relay communication station  21  of the HAPS  20  are installed at every 120° on the circumference of the radius Δd. Since the airframe of the HAPS  20  generally flies while rotating in the stratosphere, for example, as shown in  FIG.  5    described above, the FL antennas  211 ( 1 ) to  211 ( 3 ) of the relay communication station  21  control the beam so that the main beam faces the opposing GW stations  70 ( 1 ) to  70 ( 3 ). Herein, rotation angle Φ of the airframe of the HAPS  20  is a relative rotation angle with each GW station direction as 0°. With the rotation of the airframe of the HAPS  20 , the propagation path (phase mainly due to the difference in path length) of each FL antennas  211 ( 1 ) to  211 ( 3 ) on the circumference of the radius Δd changes. Since the weight W is determined by the frequency of the pilot signal (hereinafter referred to as “pilot frequency”), the amount of interference cancellation in a signal band different from the pilot frequency decreases, the larger the frequency difference and the smaller the amount of cancellation. 
       FIG.  13    is a graph showing an example of computer simulation results for evaluating interference reduction effect when the weights W are obtained at pilot frequencies different from each other. Further,  FIG.  14    is a graph showing an example of computer simulation results of a SINR characteristic of an entire transmission signal band of the feeder link in case that the airframe of the HAPS  20  is rotated. The evaluation parameters are shown in Table 1. 
     
       
         
           
               
               
               
             
               
                   
                 TABLE 1 
               
               
                   
                   
               
               
                   
                 Evaluation Parameter 
                 Value 
               
               
                   
                   
               
             
            
               
                   
                 Number of ground stations (GW stations) 
                 3 
               
            
           
           
               
               
               
               
            
               
                   
                 Disposed radius R of ground stations 
                 100 
                 km 
               
               
                   
                 (GW stations) 
               
            
           
           
               
               
               
            
               
                   
                 Number of antennas of HAPS relay 
                 3 
               
               
                   
                 communication station 
               
            
           
           
               
               
               
               
            
               
                   
                 Disposed radius r of antennas of HAPS 
                 0.5 
                 m 
               
               
                   
                 relay communication station 
               
               
                   
                 Carrier frequency 
                 3.3 
                 GHz 
               
               
                   
                 Bandwidth B of transmission signals 
                 18 
                 MHz 
               
               
                   
                 Gain of antenna 
                 20 
                 dBi 
               
               
                   
                 Front-back ratio (F/B ratio) of antenna 
                 20 
                 dB 
               
               
                   
                 S/N ratio 
                 20 
                 dB 
               
               
                   
                   
               
            
           
         
       
     
     A radius Δd of the FL antenna (relay antenna)  211  is 0.5 [m], a gain of the FL antenna  211  is 20 [dBi], and a front-back ratio (F/B ratio) is 20 [dB]. Assuming that a reception SNR of the relay communication station  21  received by an omnidirectional antenna is 20 [dB], a reception SNR of the relay communication station  21  received by the FL antenna  211  is 40 [dB]. Further, the transmission signal bandwidth of the feeder link is set to 18 [MHz]. As an example, evaluate in case that the pilot frequency is set at the edge and the center of the transmission signal bandwidth of the feeder link 
     As shown in  FIG.  13   , it is found that the amount of interference reduction in the transmission signal band of the feeder link differs depending on the pilot frequency. In case that the pilot frequency is set to the center of the transmission signal band (C 2  in the figure), interference can be reduced over the entire transmission signal bandwidth. Further, in case that the pilot frequency is set to the center of the transmission signal band (C 2  in the figure) as shown in  FIG.  14   , it is found that the SINR can be improved by 15 dB or more as compared with the case without the interference canceller. 
       FIG.  15    is an illustration showing an example of frequencies f 1 , f 2 , and f 3  of respective pilot signals in case that each of the GW stations  70 ( 1 ) to  70 ( 3 ) transmits a single pilot signal.  FIG.  16    is an illustration showing an example of a derivation model of a propagation path response of feeder links using the pilot signals in  FIG.  15   . In the illustrated example, pilot signals S P1 , S P2 , and S P3  are transmitted one by one from respective GW station  70 ( 1 ) to  70 ( 3 ). The pilot signals S P1 , S P2 , and S P3  are disposed in a first guard band GB 1  which is a first adjacent band adjacent to the transmission signal band FB of the feeder link to which the desired signals S 1 , S 2 , and S 3  are transmitted from the low frequency side. 
     For example, each of pilot signals h 11  and h 21  received by the FL antennas  211 ( 1 ) and  211 ( 2 ) of the HAPS  20  is represented by the following equations (4) and (5), and the ratio of these signals is represented by the following equation (6). 
     
       
         
           
             
               
                 
                   
                     h 
                     11 
                   
                   = 
                   
                     
                       
                          
                         
                           h 
                           11 
                         
                          
                       
                       ⁢ 
                       
                         e 
                         
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                           ⁢ 
                           
                               
                           
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                             11 
                           
                         
                       
                     
                     = 
                     
                       
                          
                         
                           h 
                           11 
                         
                          
                       
                       ⁢ 
                       
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                           ⁢ 
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                           ⁢ 
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                           ⁢ 
                           
                               
                           
                           ⁢ 
                           
                             f 
                             1 
                           
                           ⁢ 
                           
                             
                               d 
                               1 
                             
                             c 
                           
                         
                       
                     
                   
                 
               
               
                 
                   ( 
                   4 
                   ) 
                 
               
             
             
               
                 
                   
                     h 
                     21 
                   
                   = 
                   
                     
                       
                          
                         
                           h 
                           21 
                         
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                       ⁢ 
                       
                         e 
                         
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                           ⁢ 
                           
                               
                           
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                             θ 
                             21 
                           
                         
                       
                     
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                           21 
                         
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                       ⁢ 
                       
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                                 d 
                                 1 
                               
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                                 ⁢ 
                                 
                                     
                                 
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                                   d 
                                   21 
                                 
                               
                             
                             c 
                           
                         
                       
                     
                   
                 
               
               
                 
                   ( 
                   5 
                   ) 
                 
               
             
             
               
                 
                   
                     
                       h 
                       21 
                     
                     
                       h 
                       11 
                     
                   
                   = 
                   
                     
                       
                         
                            
                           
                             h 
                             21 
                           
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                             h 
                             11 
                           
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                       ⁢ 
                       
                         e 
                         
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                             ( 
                             
                               
                                 θ 
                                 21 
                               
                               - 
                               
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                                 11 
                               
                             
                             ) 
                           
                         
                       
                     
                     = 
                     
                       
                         
                            
                           
                             h 
                             21 
                           
                            
                         
                         
                            
                           
                             h 
                             11 
                           
                            
                         
                       
                       ⁢ 
                       
                         e 
                         
                           j 
                           ⁢ 
                           
                               
                           
                           ⁢ 
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                           ⁢ 
                           
                               
                           
                           ⁢ 
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                           ⁢ 
                           
                               
                           
                           ⁢ 
                           
                             f 
                             1 
                           
                           ⁢ 
                           
                             
                               
                                 
                                   Δ 
                                   ⁢ 
                                   
                                       
                                   
                                   ⁢ 
                                   
                                     d 
                                     21 
                                   
                                 
                               
                             
                             
                               
                                 c 
                               
                             
                           
                         
                       
                     
                   
                 
               
               
                 
                   ( 
                   6 
                   ) 
                 
               
             
           
         
       
     
     In the foregoing equations (4) to (6), d 1  is the path length between the GW station  70 ( 1 ) and the FL antenna  211 ( 1 ), Δd 21  is the difference in path length (path difference) between the GW station  70 ( 1 ) and each of the FL antennas  211 ( 1 ) and  211 ( 2 ), and Δd 31  is the difference in path length (path difference) between the GW station  70 ( 1 ) and each of the FL antennas  211 ( 1 ) and  211 ( 3 ). The path length between the GW station  70 ( 1 ) and the FL antenna  211 ( 2 ) is represented by d 1 +Δd 21 , and the path length between the GW station  70 ( 1 ) and the FL antenna  211 ( 3 ) is represented by d 1 +Δd 31 . 
     From the foregoing equation (6), the path difference Δd 21  can be obtained by the following equation (7). θ in the equation is the phase difference between h 21  and h 11 . Other path differences such as the route difference Δd 31  mentioned above can be obtained in the same manner. 
     
       
         
           
             
               
                 
                   
                     
                       e 
                       
                         j 
                         ⁢ 
                         
                             
                         
                         ⁢ 
                         2 
                         ⁢ 
                         
                             
                         
                         ⁢ 
                         π 
                         ⁢ 
                         
                             
                         
                         ⁢ 
                         
                           f 
                           1 
                         
                         ⁢ 
                         
                           
                             
                               
                                 Δ 
                                 ⁢ 
                                 
                                     
                                 
                                 ⁢ 
                                 
                                   d 
                                   21 
                                 
                               
                             
                           
                           
                             
                               c 
                             
                           
                         
                       
                     
                     = 
                     
                       e 
                       
                         j 
                         ⁡ 
                         
                           ( 
                           
                             
                               θ 
                               21 
                             
                             - 
                             
                               θ 
                               11 
                             
                           
                           ) 
                         
                       
                     
                   
                   ⁢ 
                   
                     
 
                   
                   ⁢ 
                   
                     
                       
                         
                           
                             Δ 
                             ⁢ 
                             
                                 
                             
                             ⁢ 
                             
                               d 
                               21 
                             
                           
                           = 
                             
                           ⁢ 
                           
                             
                               c 
                               
                                 2 
                                 ⁢ 
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                                 ⁢ 
                                 
                                     
                                 
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                                   1 
                                 
                               
                             
                             ⁢ 
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                           = 
                             
                           ⁢ 
                           
                             
                               
                                 λ 
                                 1 
                               
                               
                                 2 
                                 ⁢ 
                                 π 
                               
                             
                             ⁢ 
                             θ 
                           
                         
                       
                     
                   
                   ⁢ 
                   
                     
 
                   
                   ⁢ 
                   
                     ( 
                     
                       θ 
                       = 
                       
                         
                           θ 
                           21 
                         
                         - 
                         
                           θ 
                           11 
                         
                       
                     
                     ) 
                   
                 
               
               
                 
                   ( 
                   7 
                   ) 
                 
               
             
           
         
       
     
     The same can be obtained for the above-mentioned path difference Δd 31  and other path differences Δd 12 , Δd 13 , Δd 23 , and Δd 32 . 
     Using the path differences Δd 21 , Δd 31 , Δd 12 , Δd 13 , Δd 23 , and Δd 32  mentioned above, the propagation path response at the center frequency fsc of the transmission signal band of the feeder link can be estimated by the following equation (8). 
     
       
         
           
             
               
                 
                   
                     H 
                     p 
                   
                   = 
                   
                     [ 
                     
                       
                         
                           
                              
                             
                               h 
                               11 
                             
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                                 h 
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                                 ⁢ 
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                                 ⁢ 
                                 
                                     
                                 
                                 ⁢ 
                                 
                                   f 
                                   2 
                                 
                                 ⁢ 
                                 
                                   
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                                     ⁢ 
                                     
                                         
                                     
                                     ⁢ 
                                     
                                       d 
                                       32 
                                     
                                   
                                   c 
                                 
                               
                             
                           
                         
                         
                           
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                               h 
                               33 
                             
                              
                           
                         
                       
                     
                     ] 
                   
                 
               
               
                 
                   ( 
                   8 
                   ) 
                 
               
             
           
         
       
     
     However, in case that each of the GW stations  70 ( 1 ) to  70 ( 3 ) transmits one pilot signal S P1 , S P2 , S P3  in the first guard band GB 1  as shown in  FIG.  15    and FIG.  16 , it is not possible to detect a path difference equal to or more than the wavelengths λ 1 , λ 2 , λ 3  of each pilot signal. For example, assuming that the frequency f 1  of the pilot signal S P1  of the GW station  70 ( 1 ) is 3.3 GHz, Δd 21  can be estimated only in the range of 0&lt;Δd 21 &lt;0.09 [m]. 
     Therefore, in the present embodiment, plural pilot frequencies with frequencies different from each other are transmitted from each of the GW stations  70 ( 1 ) to  70 ( 3 ) so that the path difference equal to or more than the wavelengths λ 1 , λ 2 , λ 3  of each pilot signal S P1 , S P2 , S P3  can be detected. In the example of the following embodiments, although it is illustrated regarding a case in which each of the GW stations  70 ( 1 ) to  70 ( 3 ) transmits two (plural) pilot signals with frequencies different from each other, the number of pilot signals transmitted by each of the GW stations  70 ( 1 ) to  70 ( 3 ) may be 3 or more. Further, the number of pilot signals may be different from each other between the GW stations  70 ( 1 ) to  70 ( 3 ). 
       FIG.  17    is an illustration showing an example of frequency arrangement of respective pilot signals when the plural GW stations  70 ( 1 ) to  70 ( 3 ) respectively transmit plural pilot signals.  FIG.  18    is an illustration showing an example of a derivation model of the propagation path response of the feeder link using the pilot signals in  FIG.  17   . In the illustrated example, plural pilot signals transmitted from each of the GW station  70 ( 1 ) to  70 ( 3 ) are distributed and disposed in each of a first guard band GB 1 , which is a first adjacent band adjacent to the transmission signal band FB of the feeder link to which the desired signals S 1 , S 2 , S 3  are transmitted from the GW stations  70 ( 1 ) to  70 ( 3 ) from the low frequency side and the high frequency side, and a second guard band GB 2  which is a second adjacent band. Specifically, pilot signals S P1 , S P2 , S P3 , which are transmitted from respective GW station  70 ( 1 ) to  70 ( 3 ) with frequencies f 1 , f 2 , f 3  different from each other, are disposed in the first guard band GB 1 . Further, pilot signals S P1 ′, S P2 ′, S P3 ′, which are transmitted from respective GW station  70 ( 1 ) to  70 ( 3 ) with frequencies f 1 ′, f 2 ′, f 3 ′ different from each other, are disposed in the second guard band GB 2 . The relay communication station  21  of the HAPS  20  separates each of the plural pilot signals S P1 , S P2 , S P3  of the first guard band GB 1  received from the GW stations  70 ( 1 ),  70 ( 2 ) and  70 ( 3 ) by a filter, and separates each of the plural pilot signals S P1 ′, S P2 ′, S P3 ′ of the second guard band GB 2  received from the GW stations  70 ( 1 ),  70 ( 2 ) and  70 ( 3 ) by a filter. 
     For example, each of the pilot signals h 11 , h 11 ′, h 21  and h 21 ′ received by the FL antennas  211 ( 1 ) and  211 ( 2 ) of the HAPS  20  is represented by the following equations (9), (10), (11) and (12), and each of the ratios of these signals is represented by the following equations (13) and (14). 
     
       
         
           
             
               
                 
                   
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                   11 
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                                 21 
                               
                             
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                   ( 
                   14 
                   ) 
                 
               
             
           
         
       
     
     In the equations (9) to (14), d 1  is the path length between the GW station  70 ( 1 ) and the FL antenna  211 ( 1 ), and Δd 21  is the difference in path length (path difference) between the GW station  70 ( 1 ) and each of the FL antennas  211 ( 1 ) and  211 ( 2 ). The path length between the GW station  70 ( 1 ) and the FL antenna  211 ( 2 ) is represented by d 1 +Δd 21 . 
     From the equations (13) and (14), the path difference Δd 21  can be obtained by the following equation (15). Note that θ in the equation (15) is a phase difference obtained by adding the phase difference between h 11 ′ and h 11  and the phase difference between h 21  and h 21 ′. That is, θ=(phase difference between h 11 ′ and h 11 )+(phase difference between h 21  and h 21 ′). 
     
       
         
           
             
               
                 
                   
                     
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                   15 
                   ) 
                 
               
             
           
         
       
     
     Path difference Δd 31  and other path differences Δd 12 , Δd 13 , Δd 23 , Δd 32  between the GW station  70 ( 1 ) and each of the FL antennas  211 ( 1 ) and  211 ( 3 ) can be similarly obtained. 
     Using the path differences Δd 21 , Δd 31 , Δd 12 , Δd 13 , Δd 23 , and Δd 32  mentioned above, the propagation path response at the center frequency fsc of the transmission signal band of the feeder link can be estimated as in the foregoing equation (8). 
     In case that each of the GW stations  70 ( 1 ) to  70 ( 3 ) transmits the plural pilot signals as shown in  FIG.  17    and  FIG.  18   , it is possible to detect a path difference equal to or more than the wavelengths λ 1 , λ 2 , λ 3  of each pilot signal. For example, assuming the LTE, the bandwidth B of the transmission signal band FB of the feeder link is 18 MHz, so that Δd 21  can be estimated in the range within the wavelength of the pilot frequency difference B as shown in the equation (15). In the present example, it can be estimated accurately up to the range of 0&lt;Δd 21 &lt;16 [m], which is a range required for implementing. 
     Further, in the examples in  FIG.  17    and  FIG.  18   , since the plural pilot signals S P1 , S P2 , S P3  and pilot signals S P1 ′, S P2 ′, S P3 ′, which are transmitted from respective GW station  70 ( 1 ) to  70 ( 3 ) with frequencies f 1 , f 2 , f 3 , f 2 ′, f 3 ′ different from each other, are evenly distributed and disposed in the first guard band GB 1  and the second guard band GB 2 , each pilot signal can be separated by the filter and easily individually detected. 
       FIG.  19    is an illustration showing another example of arrangement of pilot signals when the plural GW stations  70 ( 1 ) to  70 ( 3 ) respectively transmit plural pilot signals. In the illustrated example, it is an example in which the plural pilot signals S P1 , S P2 , S P3  and pilot signals S P1 ′, S P2 ′, S P3 ′ transmitted from the GW stations  70 ( 1 ) to  70 ( 3 ) with frequencies f 1 , f 2 , f 3 , f 2 ′, f 3 ′ different from each other are all disposed in the first guard band GB 1 . The relay communication station  21  of the HAPS  20  filters each of the plural pilot signals S P1 , S P2 , S P3 , S P1 ′, S P2 ′, and S P3 ′ of the first guard band GB 1  received from the GW stations  70 ( 1 ) to  70 ( 3 ) by the filter. 
       FIG.  20    is an illustration showing yet another example of arrangement of pilot signals when the plural GW stations  70 ( 1 ) to  70 ( 3 ) respectively transmit plural pilot signals. The illustrated example is an example in which the numbers of pilot signals disposed in the first guard band GB 1  and the second guard band GB 2  are different from each other. Specifically, pilot signals S P1  and S P1 ′, which are transmitted from the GW station  70 ( 1 ) with frequencies f 1  and different from each other, are disposed in the first guard band GB 1 , and pilot signals S P2 , S P2 ′, S P3 , S P3 ′, which transmitted from GW stations  70 ( 2 ) and  70 ( 3 ) with frequencies f 2 , f 2 ′, f 3 , f 3 ′ different from each other, are disposed in the second guard band GB 2 . The relay communication station  21  of the HAPS  20  separates each of the plural pilot signals S P1  and S P1 ′ of the first guard band GB 1  received from the GW station  70 ( 1 ) by the filter, and separates each of the plural pilot signals S P2 , S P2 ′, S P3 , S P3 ′ of the second guard band GB 2  received from the GW stations  70 ( 2 ) and  70 ( 3 ) by the filter. 
     In particular, in an arrangement example of the pilot signal in  FIG.  20   , the pilot signals SPi and SPi′ transmitted from respective GW station  70 ( i ) (i=1, 2, 3) are disposed in the same guard band. Specifically, the pilot signals S P1 , S P1 ′ transmitted from the GW station  70 ( 1 ) are disposed in the first guard band GB 1 , and the pilot signals S P2 , S P2 ′, S P2 , S P3 , S P3 ′ transmitted from the GW stations  70 ( 2 ) and  70 ( 3 ) are disposed in the second guard band GB 2 . When the pilot signals S Pi , S P i′ transmitted from the same GW station  70 ( i ) at frequencies f 1  and f 1 ′ are disposed in the same guard band in this way, the frequency difference of f 1 -f 1 ′ becomes small, so that the estimated distance of Δd 21  becomes large as shown in the foregoing equation (15). 
     It is noted that, the weight used for the interference canceller using the matrix Hfc of the propagation path response can be calculated by, for example, the ZF (Zero-Forcing) method or the MMSE (Minimum Mean Square Error) method using the matrix of the propagation path response. 
     For example, in the ZF method, the weight W can be obtained by the inverse matrix of the matrix H fc  of the propagation path response as in the following equation (16).
 
 W=H   P   −1 ( f   f     SC   )  (16)
 
     Further, in the MMSE method, the weight W can be used by the following equation (17). Herein, N T  is the number of transmission antennas and γ is the SNR. 
     
       
         
           
             
               
                 
                   W 
                   = 
                   
                     
                       
                         ( 
                         
                           
                             
                               
                                 H 
                                 P 
                                 H 
                               
                               ⁡ 
                               
                                 ( 
                                 
                                   f 
                                   
                                     S 
                                     ⁢ 
                                     C 
                                   
                                 
                                 ) 
                               
                             
                             ⁢ 
                             
                               
                                 H 
                                 P 
                               
                               ⁡ 
                               
                                 ( 
                                 
                                   f 
                                   SC 
                                 
                                 ) 
                               
                             
                           
                           + 
                           
                             
                               
                                 N 
                                 T 
                               
                               ⁢ 
                               
                                 I 
                                 
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                             γ 
                           
                         
                         ) 
                       
                       
                         - 
                         1 
                       
                     
                     ⁢ 
                     
                       
                         H 
                         P 
                         H 
                       
                       ⁡ 
                       
                         ( 
                         
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                   ( 
                   17 
                   ) 
                 
               
             
           
         
       
     
     In the examples of  FIG.  12    to  FIG.  20    shown above, the propagation path response Hs(fi) at one estimation frequency fi in the transmission signal band FB is estimated from the pilot signals received from the GW stations, and the weight Wp is derived based on the propagation path response Hs(fi) at the estimation frequency fi. Ss′ (signal to be subtracted from the reception signal from the target GW station) obtained by multiplying the wait Wp by the reception signal Es from another GW station is calculated by, for example, the following equation (18). In the equation, Ss is a transmission signal transmitted from another GW station, N is noise, and Hs(fs) is a propagation path response at the transmission frequency fs of the transmission signal Ss in the transmission signal band FB.
 
 S   S ( t )′= W   P   E   S ( t )= H   P   −1 ( f   SC )( H   S )( f   S ) S   S ( t )+ N ( t ))=( H   P   −1 ( f   SC ) H   S ( f   S )) S   S ( t )+ H   P   −1 ( f   SC ) N ( t )   (18)
 
     In the equation (18), in case that the estimation frequency fi and the transmission frequency fs are equal to each other (fi=fs), (Hs(fi) −1 Hs(fs)) Ss becomes the identity matrix I, so that the interference suppression amount (interference cancellation amount) becomes maximum, and the larger the difference (Δfi) between the estimation frequency fi and the transmission frequency fs, the smaller the interference suppression amount (interference cancellation amount). For example, in case that the estimation frequency fi, at which the propagation path response Hs(fi) is estimated, is located at the center frequency fsc of the transmission signal band FB of the feeder link as shown in C 1  of  FIG.  21   , the interference suppression amount (interference cancellation amount) ΔIs becomes maximum when the transmission frequency fs is the center frequency fsc, and the closer the transmission frequency fs approaches the end portion of the transmission signal band FB, the larger the Δfi becomes, and the more the amount of interference suppression (interference cancellation amount) decreases, and Δfi becomes maximum and ΔIs becomes minimum at the end. In case that the estimation frequency fi, at which the propagation path response Hs(fi) is estimated, is located at the low-frequency side end (fsc−B/2) of the transmission signal band FB of the feeder link as shown in C 2  of  FIG.  21   , Δfi becomes maximum, the interference suppression amount (interference cancellation amount) becomes maximum when the transmission frequency fs is located at the low-frequency side end (fsc−B/2), and the closer the transmission frequency fs approaches the high frequency side end (fsc+B/2) of the transmission signal band FB, the more Δfi increases and the more the interference suppression amount (interference cancellation amount) ΔIs decreases, and Δfi becomes maximum and ΔIs becomes minimum at the side end. In case that the transmission frequency fs is the center frequency fsc, the maximum value of Δfi is the minimum and the minimum value of ΔIs is the maximum, so that the interference reduction effect is most highly enhanced. 
     Therefore, in the present embodiment, in order to increase the interference suppression amount (interference cancellation amount) over the entire transmission signal band FB, the transmission signal band FB with the entire bandwidth B is divided into plural (n) frequency bands (hereinafter, referred to as “divided frequency bands”) FB 1  to FBn with bandwidth B/n, and an interference suppression processing between feeder links including the estimation of the propagation path response H and the calculation of the weight W is performed as shown in  FIG.  22    and the following (1) to (3). 
     (1) Estimation of the propagation path response for each divided frequency band: 
     Plural propagation path responses H(fsc 1 ) to H(fscn) between each of the plural GW stations  70 ( 1 ) to  70 ( 3 ) and the antennas for feeder link  211 ( 1 ) to  211 ( 3 ) of the HAPS  20  are estimated for each of the plural divided frequency bands FB 1  to FBn, by setting the center frequencies fsc 1  to Fscn of each of the plural divided frequency bands FB 1  to FBn as the estimation frequency fi, based on the reception results of the pilot signals received from each of the plural GW stations  70 ( 1 ) to  70 ( 3 ). 
     (2) Calculation of the Weight for Each Divided Frequency: 
     With respect to each of the plural GW stations  70 ( 1 ) to  70 ( n ), weights Wp 1  to Wpn for suppressing each interference signal that causes interference by the transmission signal transmitted from each GW station and received with the directional beams corresponding to the other GW stations, are calculated for each divided frequency band (FB 1  to FBn) divided into n, based on the plural propagation path responses H(fsc 1 ) to H(fscn). 
     (3) Interference-Canceling Signal Processing for Each Divided Frequency: 
     With respect to each of the plural GW stations  70 ( 1 ) to  70 ( 3 ), the reception signals received by the directional beams corresponding to the other GW stations are respectively multiplied by the weights Wp 1  to Wpn corresponding to the other GW stations and subtracted from the reception signal received by the directional beam corresponding to each GW station, for each of the divided frequency bands FB 1  to FBn divided into n. 
     Herein, assuming that the reception signals in the plural divided frequency bands FB 1  to FBn are Es 1  to Esn, Ss′ (signal to be subtracted from the reception signal from the target GW station) is calculated by, for example, the following equation (19). Ss in the equation is a transmission signal transmitted from another GW station, and N is noise. The Hs(fsc 1 ) to Hs(fscn) are propagation path responses, which are respectively estimated by setting the center frequencies fsc 1  to fscn of the divided frequency bands FB 1  to FBn as estimation frequencies. Further, the Hs (fs 1 ) to Hs (fsn) are propagation path responses at the transmission frequencies fs 1  to fsn of the transmission signal Ss in the divided frequency bands FB 1  to FBn, respectively. 
     
       
         
           
             
               
                 
                   
                     
                       
                         
                           
                             
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                             ⁡ 
                             
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     By dividing the transmission signal band FB of the feeder link into the plural divided frequency bands FB 1  to FBn, and performing an interference suppression processing between feeder links including the estimation of the propagation path response H and the calculation of the weight W, the difference (Δfi) between the estimation frequency fi that estimated the propagation path response H and the transmission frequency fs of the feeder link becomes smaller, and the interference suppression amount (interference cancellation amount) ΔIs can be increased over the entire transmission signal band FB as shown in  FIG.  22   . 
       FIG.  23    is a graph showing an example of a relationship between the number of divisions (n) of the transmission signal band FB and the SINR [dB] when receiving the feeder link of the HAPS  20  in the feeder-link interference suppression processing according to the present embodiment. The vertical axis in the figure is an average value of SINR [dB] when the HAPS  20  makes one rotation (see  FIG.  5    to  FIG.  7   ). As shown in  FIG.  23   , when the number of divisions (n) of the transmission signal band FB of the feeder link increases, the interference suppression effect between the feeder links is enhanced, and the communication quality (SINR) of the feeder link is improved. 
     It is noted that, although the transmission signal band FB of the feeder link is evenly divided in the example of  FIG.  22   , the transmission signal band FB of the feeder link may be unequally divided. The unequal division of the transmission signal band FB may be performed according to the distribution of the interference signals of the feeder link in the transmission signal band FB of the feeder link. For example, as shown in  FIG.  24   , only the band FB 1  including large number of or high-intensity interference signals of the feeder link among the transmission signal band FB may be divided to enhance the interference suppression effect, and the remaining band FB 2  with small number of or low-intensity interference signals of the feeder link may not be divided. 
       FIG.  25    is an illustration showing an example of a main configuration of the relay communication station  21  of the HAPS  20  according to the embodiment. In  FIG.  25   , the relay communication station  21  is provided with a feeder-link communication section  221 , a service-link communication section  222 , a frequency conversion section  223 , a control section  224  that controls each section, and an interference suppression section  225 . 
     The feeder-link communication section  221  transmits and receives radio signals of a first frequency F 1  for feeder link to and from the GW station  70  via the FL antenna  211 . Further, the feeder-link communication section  221  receives plural pilot signals transmitted from each of the plural GW stations  70 ( 1 ) to  70 ( 3 ), and separates each of the received plural pilot signals by the filter. The service-link communication section  222  transmits and receives radio signals of a second frequency F 2  for the service link to and from the terminal apparatus  61  via the service link antenna  115 . The frequency conversion section  223  performs a frequency conversion between the first frequency F 1  and the second frequency F 2  between the feeder-link communication section  221  and the service-link communication section  222 . The radio signals relayed by the relay communication station  21  may be transmitted and received, for example, by using the OFMDA communication method conforming to the LTE or LTE-Advanced standard. In this case, good communication quality can be maintained even if multipaths with different radio signal delays occur. 
     The control section  224  can control each section by executing a program incorporated in advance. 
     The interference suppression section  225  performs the above-mentioned (1) estimation of the propagation path response for each divided frequency band, (2) calculation of the weight for each divided frequency, and (3) interference-canceling signal processing for each divided frequency, by executing a program incorporated in advance. 
     It is noted that, in case of receiving control information from the remote control apparatus (control source) of the communication operator of the mobile communication network or transmitting information to the remote control apparatus, a user terminal (mobile station)  226  connected to the control section  224  may be provided. The control section  224 , for example, may receive control information transmitted from the remote control apparatus by the user terminal (mobile station)  226  and control each section based on the control information. Herein, the communication between the remote control apparatus and the user terminal (mobile station)  226  may be performed using, for example, the IP address (or telephone number) assigned to each of the remote control apparatus and the user terminal (mobile station)  226 . 
     As described above, according to the present embodiment, it is possible to suppress the interferences in the multiple feeder links of the same frequency between the HAPS  20  and the plural GW stations  70 ( 1 ) to  70 ( 3 ). 
     In particular, according to the present embodiment, by dividing the transmission signal band FB of the feeder link into the plural divided frequency bands, estimating the propagation path response, calculating the weight W and processing the interference canceling signal using the weight W for each divided frequency band, the minimum value of the interference suppression amount (interference cancellation amount) ΔIs in the entire transmission signal band FB can be lowered, and the interference suppression effect can be enhanced. 
     Further, according to the present embodiment, by transmitting plural pilot signals S P1 , S P2 , S P3 , S P1 ′, S P2 ′, S P3 ′ with frequencies different from each other from each of the plural GW stations  70 ( 1 ) to  70 ( 3 ), the path difference between the HAPS  20  and the plural GW stations  70 ( 1 ) to  70 ( 3 ) required for the dynamic suppression of interferences in the multiple feeder links can be estimated and grasped up to the range required for implementing, so that the interferences in the multiple feeder link can be suppressed accurately. 
     Further, according to the present embodiment, it is possible to improve the frequency utilization efficiency of the feeder link while suppressing the decrease in the SINR of the feeder links of the HAPS  20 . 
     It is noted that, the process steps and configuration elements of the relay communication station of the communication relay apparatus such as the HAPS, the feeder station, the gateway station, the management apparatus, the monitoring apparatus, the remote control apparatus, the server, the terminal apparatus (user apparatus, mobile station, communication terminal), the base station and the base station apparatus described in the present description can be implemented with various means. For example, these process steps and configuration elements may be implemented with hardware, firmware, software, or a combination thereof. 
     With respect to hardware implementation, means such as processing units or the like used for establishing the foregoing steps and configuration elements in entities (for example, radio relay station, feeder station, gateway station, base station, base station apparatus, radio-relay station apparatus, terminal apparatus (user apparatus, mobile station, communication terminal), management apparatus, monitoring apparatus, remote control apparatus, server, hard disk drive apparatus, or optical disk drive apparatus) may be implemented in one or more of an application-specific IC (ASIC), a digital signal processor (DSP), a digital signal processing apparatus (DSPD), a programmable logic device (PLD), a field programmable gate array (FPGA), a processor, a controller, a microcontroller, a microprocessor, an electronic device, other electronic unit, computer, or a combination thereof, which are designed so as to perform a function described in the present specification. 
     With respect to the firmware and/or software implementation, means such as processing units or the like used for establishing the foregoing configuration elements may be implemented with a program (for example, code such as procedure, function, module, instruction, etc.) for performing a function described in the present specification. In general, any computer/processor readable medium of materializing the code of firmware and/or software may be used for implementation of means such as processing units and so on for establishing the foregoing steps and configuration elements described in the present specification. For example, in a control apparatus, the firmware and/or software code may be stored in a memory and executed by a computer or processor. The memory may be implemented within the computer or processor, or outside the processor. Further, the firmware and/or software code may be stored in, for example, a medium capable being read by a computer or processor, such as a random-access memory (RAM), a read-only memory (ROM), a non-volatility random-access memory (NVRAM), a programmable read-only memory (PROM), an electrically erasable PROM (EEPROM), a FLASH memory, a floppy (registered trademark) disk, a compact disk (CD), a digital versatile disk (DVD), a magnetic or optical data storage unit, or the like. The code may be executed by one or more of computers and processors, and a certain aspect of functionalities described in the present specification may by executed by a computer or processor. 
     The medium may be a non-transitory recording medium. Further, the code of the program may be executable by being read by a computer, a processor, or another device or an apparatus machine, and the format is not limited to a specific format. For example, the code of the program may be any of a source code, an object code, and a binary code, and may be a mixture of two or more of those codes. 
     The description of embodiments disclosed in the present specification is provided so that the present disclosures can be produced or used by those skilled in the art. Various modifications of the present disclosures are readily apparent to those skilled in the art and general principles defined in the present specification can be applied to other variations without departing from the spirit and scope of the present disclosures. Therefore, the present disclosures should not be limited to examples and designs described in the present specification and should be recognized to be in the broadest scope corresponding to principles and novel features disclosed in the present specification. 
     REFERENCE SIGNS LIST 
     
         
           20  HAPS (communication relay apparatus) 
           21  relay communication station 
           61  terminal apparatus 
           70 ,  70 ( 1 ) to  70 ( 3 ) gate way station (GW station) 
           71 ,  71 ( 1 ) to  71 ( 3 ) antenna for feeder link (GW antenna) 
           200 C,  200 C( 1 ) to  200 C( 7 ) three dimensional cell 
           200 F,  200 F( 1 ) to  200 F( 7 ) foot print 
           211 ,  211 ( 1 ) to  211 ( 3 ) antenna for feeder link (FL antenna) 
           212 ,  212 ( 1 ) to  212 ( 3 ) antenna directional beam 
           215  antenna for service link (SL antenna