Patent Publication Number: US-7907689-B2

Title: Broadcast transmission with spatial spreading in a multi-antenna communication system

Description:
CLAIM OF PRIORITY 
     The present application for patent is a divisional application of, and claims priority from, U.S. patent application Ser. No. 11/009,824, entitled “Broadcast Transmission with Spatial Spreading in a Multi-Antenna Communication System” and filed on Dec. 9, 2004, which claims the benefit of priority from U.S. Provisional Patent Application Ser. No. 60/530,860, entitled “Broadcast Transmission with Pseudo-Random Transmit Steering in a Multi-Antenna Communication System” and filed on Dec. 17, 2003, both of which are assigned to the assignee hereof and both of which are fully incorporated herein by reference for all purposes. 
    
    
     BACKGROUND 
     I. Field 
     The present invention relates generally to communication, and more specifically to techniques for broadcasting data in a multi-antenna communication system. 
     II. Background 
     A multi-antenna communication system employs multiple transmit antennas at a transmitting entity and one or more receive antennas at a receiving entity for data transmission. The multi-antenna communication system may thus be a multiple-input multiple-output (MIMO) system or a multiple-input single-output (MISO) system. A MIMO system employs multiple (NT) transmit antennas and multiple (NR) receive antennas for data transmission. A MIMO channel formed by the NT transmit antennas and the NR receive antennas may be decomposed into NS spatial channels, where N S ≦min {N T , N R }. The NS spatial channels may be used to transmit data in a manner to achieve greater reliability and/or higher overall throughput. A MISO system employs multiple (NT) transmit antennas and a single receive antenna for data transmission. A MISO channel formed by the NT transmit antennas and the single receive antenna is composed of a single spatial channel. 
     An access point in a MIMO system may broadcast data to a number of multi-antenna user terminals, which may be distributed throughout the coverage area of the access point. A different MIMO channel is formed between the access point and each of these user terminals. Each MIMO channel may experience different channel conditions (e.g., different fading, multipath, and interference effects). Consequently, the spatial channels of each MIMO channel may achieve different signal-to-noise-and-interference ratios (SNRs). The SNR of a spatial channel determines its transmission capacity, which is typically quantified by a particular data rate that may be reliably transmitted on the spatial channel. For a time variant MIMO channel, the channel condition changes over time and the SNR of each spatial channel also changes over time. 
     A broadcast transmission is a data transmission that is intended to be received by any number of user terminals in the system, instead of a specific user terminal. A broadcast transmission is typically encoded and transmitted in a manner to achieve a specified quality of service (QoS). This quality of service may be quantified, for example, by error free reception of the broadcast transmission by a particular percentage (e.g., 99.9%) of the user terminals within a given broadcast coverage area at any given moment. Equivalently, the quality of service may be quantified by an “outage” probability, which is the percentage (e.g., 0.11%) of the user terminals within the broadcast coverage area that cannot correctly decode the broadcast transmission. 
     The broadcast transmission observes an ensemble of MIMO channels for an ensemble of user terminals in the broadcast coverage area. The MIMO channel for each user terminal may be random with respect to the MIMO channels for other user terminals. Furthermore, the MIMO channels for the user terminals may vary over time. To ensure that the broadcast transmission can meet the specified quality of service, the data rate for the broadcast transmission is typically selected to be sufficiently low so that the broadcast transmission can be reliably decoded even by the user terminal with the worst channel condition (i.e., the worst-case user terminal). The broadcast performance for such a system would then be dictated by the expected worst-case channel condition for all of the user terminals in the system. A similar phenomenon occurs for a MISO system. 
     There is therefore a need in the art for techniques to more efficiently broadcast data in a multi-antenna communication system. 
     SUMMARY 
     In one embodiment, a method for broadcasting data in a wireless multi-antenna communication system is described in which at least one block of data is processed to obtain at least one block of data symbols. Spatial processing is performed on the at least one block of data symbols with a plurality of steering matrices to obtain a plurality of sequences of transmit symbols. The plurality of sequences of transmit symbols is broadcasted from a plurality of transmit antennas to a plurality of receiving entities in the system, wherein the plurality of steering matrices randomize an effective channel observed by each of the plurality of receiving entities for the at least one block of data symbols. 
     In another embodiment, an apparatus in a wireless multi-antenna communication system is described which includes a data processor to process at least one block of data to obtain at least one block of data symbols; a spatial processor to perform spatial processing on the at least one block of data symbols with a plurality of steering matrices to obtain a plurality of sequences of transmit symbols; and a plurality of transmitter units to broadcast the plurality of sequences of transmit symbols from a plurality of transmit antennas to a plurality of receiving entities in the system, wherein the plurality of steering matrices randomize an effective channel observed by each of the receiving entities for the at least one block of data symbols. 
     In another embodiment, an apparatus in a wireless multi-antenna communication system is described which includes means for processing at least one block of data to obtain at least one block of data symbols; means for performing spatial processing on the at least one block of data symbols with a plurality of steering matrices to obtain a plurality of sequences of transmit symbols; and means for broadcasting the plurality of sequences of transmit symbols from a plurality of transmit antennas to a plurality of receiving entities in the system, wherein the plurality of steering matrices randomize an effective channel observed by each of the receiving entities for the at least one block of data symbols. 
     In another embodiment, a method for broadcasting data in a wireless multi-antenna communication system is described in which a plurality of data streams is processed to obtain a plurality of blocks of data symbols, wherein each block of data symbols corresponds to one block of coded data. Spatial processing is performed on the plurality of blocks of data symbols with a plurality of steering matrices to obtain a plurality of sequences of transmit symbols. The plurality of sequences of transmit symbols is broadcasted from a plurality of transmit antennas to a plurality of receiving entities in the system, wherein the plurality of steering matrices randomize an effective channel observed by each of the plurality of receiving entities for the plurality of blocks of data symbols. 
     In another embodiment, a method for receiving a broadcast transmission in a wireless multi-antenna communication system is described in which, via a plurality of receive antennas, received data symbols are obtained for at least one data symbol block spatially processed with a plurality of steering matrices prior to broadcast from a plurality of transmit antennas to a plurality of receiving entities. A channel estimate is obtained for an effective multiple-input multiple-output (MIMO) channel formed by the plurality of steering matrices and a MIMO channel between the plurality of transmit antennas and the plurality of receive antennas. Receiver spatial processing is performed on the received data symbols with the channel estimate to obtain data symbol estimates for the at least one data symbol block. 
     In another embodiment, an apparatus in a wireless multi-antenna communication system is described which includes a plurality of receiver units to obtain, via a plurality of receive antennas, received data symbols for at least one data symbol block spatially processed with a plurality of steering matrices prior to broadcast from a plurality of transmit antennas to a plurality of receiving entities; a channel estimator to obtain a channel estimate for an effective multiple-input multiple-output (MIMO) channel formed by the plurality of steering matrices and a MIMO channel between the plurality of transmit antennas and the plurality of receive antennas; and a spatial processor to perform receiver spatial processing on the received data symbols with the channel estimate to obtain data symbol estimates for the at least one data symbol block. 
     In another embodiment, an apparatus in a wireless multi-antenna communication system is described which includes means for obtaining, via a plurality of receive antennas, received data symbols for at least one data symbol block spatially processed with a plurality of steering matrices prior to broadcast from a plurality of transmit antennas to a plurality of receiving entities; means for obtaining a channel estimate for an effective multiple-input multiple-output (MIMO) channel formed by the plurality of steering matrices and a MIMO channel between the plurality of transmit antennas and the plurality of receive antennas; and means for performing receiver spatial processing on the received data symbols with the channel estimate to obtain data symbol estimates for the at least one data symbol block. 
     In another embodiment, a method for receiving a broadcast transmission in a wireless multi-antenna communication system is described in which, via a single receive antenna, received data symbols are obtained for a data symbol block spatially processed with a plurality of steering vectors prior to broadcast from a plurality of transmit antennas to a plurality of receiving entities. A channel estimate is obtained for an effective multiple-input single-output (MISO) channel formed by the plurality of steering vectors and a MISO channel between the plurality of transmit antennas and the single receive antenna. Detection on the received data symbols is performed with the channel estimate to obtain data symbol estimates for the data symbol block. 
     In another embodiment, an apparatus in a wireless multi-antenna communication system is described which includes a receiver unit to obtain, via a single receive antenna, received data symbols for a data symbol block spatially processed with a plurality of steering vectors prior to broadcast from a plurality of transmit antennas to a plurality of receiving entities; a channel estimator to obtain a channel estimate for an effective multiple-input single-output (MISO) channel formed by the plurality of steering vectors and a MISO channel between the plurality of transmit antennas and the single receive antenna; and a detector to perform detection on the received data symbols with the channel estimate to obtain data symbol estimates for the data symbol block. 
     In another embodiment, an apparatus in a wireless multi-antenna communication system is described which includes means for obtaining, via a single receive antenna, received data symbols for a data symbol block spatially processed with a plurality of steering vectors prior to broadcast from a plurality of transmit antennas to a plurality of receiving entities; means for obtaining a channel estimate for an effective multiple-input single-output (MISO) channel formed by the plurality of steering vectors and a MISO channel between the plurality of transmit antennas and the single receive antenna; and means for performing detection on the received data symbols with the channel estimate to obtain data symbol estimates for the data symbol block. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         FIG. 1  shows a MIMO system with an access point and multi-antenna user terminals. 
         FIG. 2  shows a process for broadcasting data with spatial spreading. 
         FIG. 3  shows a process for receiving a broadcast transmission. 
         FIG. 4  shows a block diagram of the access point and multi-antenna user terminal. 
         FIGS. 5A and 5B  show two embodiments of a transmit (TX) data processor and a TX spatial processor at the access point. 
         FIGS. 6A and 6B  show two embodiments of a receive (RX) spatial processor and an RX data processor at the multi-antenna user terminal. 
         FIG. 7  shows a MISO system with an access point and single-antenna user terminals. 
         FIG. 8  shows a block diagram of the access point and single-antenna user terminal. 
         FIG. 9  shows a hybrid multi-antenna system with an access point and single-antenna and multi-antenna user terminals. 
         FIGS. 10A and 10B  show plots of overall spectral efficiency achieved for a 4×4 MIMO system and a 4×1 MISO system, respectively. 
     
    
    
     DETAILED DESCRIPTION 
     The word “exemplary” is used herein to mean “serving as an example, instance, or illustration.” Any embodiment described herein as “exemplary” is not necessarily to be construed as preferred or advantageous over other embodiments. 
     Techniques for broadcasting data using spatial spreading in a multi-antenna communication system are described herein. Spatial spreading refers to the transmission of a data symbol (which is a modulation symbol for data) from multiple transmit antennas simultaneously, possibly with different amplitudes and/or phases determined by a steering vector used for that data symbol. Spatial spreading may also be called transmit steering, pseudo-random transmit steering, steering diversity, matrix pseudo-random steering, vector pseudo-random steering, and so on. As used herein, “broadcast” refers to data transmission to either (1) an unspecified group of user terminals, e.g., all user terminals within a broadcast coverage area (which is commonly referred to as broadcast) or (2) a specific group of user terminals (which is commonly referred to as multi-cast). These broadcast transmission techniques can randomize an “effective” channel observed by each user terminal for each block of data symbols broadcast by an access point, so that system performance is not dictated by the expected worst-case channel condition. 
     In an embodiment for broadcasting data with spatial spreading, data for ND data streams is processed (e.g., encoded, interleaved, and modulated) to obtain ND data symbol blocks to be broadcast in NM transmission spans, where N D &gt;1 and N M &gt;1. A “transmission span” can cover time and/or frequency dimensions, as described below. Each data symbol block is generated from a block of coded data, which may be referred to as a “code block” or coded data packet. Each code block is encoded separately at the access point and decoded separately at a user terminal. The ND data symbol blocks are partitioned into NM data symbol subblocks, one subblock for each transmission span. A steering matrix is selected (e.g., in a deterministic or pseudo-random manner from among a set of L steering matrices) for each of the NM data symbol subblocks. Each data symbol subblock is spatially processed with the steering matrix selected for that subblock to obtain transmit symbols. The transmit symbols for each subblock are further processed and broadcast via NT transmit antennas in one transmission span to user terminals within the broadcast coverage area. 
     For a MIMO broadcast, each steering matrix contains NT rows and NS columns, where N S &gt;1. The ND data symbol blocks are then broadcast via NS spatial channels of an effective MIMO channel. For example, if N D =N S , then the ND data symbol blocks may be multiplexed such that one data symbol block is broadcast on each of the NS spatial channels. For a MISO broadcast, each steering matrix contains NT rows and a single column and may be considered as a degenerative matrix or vector. The ND data symbol blocks are then broadcast via a single spatial channel of an effective MISO channel. For both MIMO and MISO broadcasts, the ND data symbol blocks are spatially processed with NM steering matrices and observe an ensemble of effective channels at each user terminal. 
     Various aspects and embodiments of the invention are described in further detail below. 
     The broadcast transmission techniques described herein may be used for a multi-antenna communication system, which may be a MIMO system or a MISO system. As used herein, “MIMO broadcast” refers to broadcast transmission on multiple spatial channels, and “MISO broadcast” refers to a broadcast transmission on a single spatial channel. The number of spatial channels available for transmission is determined by the number of transmit antennas, the number of receive antennas, and the wireless link or channel. The broadcast transmission techniques may also be used for single-carrier and multi-carrier systems. Multiple carriers may be provided by orthogonal frequency division multiplexing (OFDM) or some other constructs. OFDM effectively partitions the overall system bandwidth into multiple (NF) orthogonal frequency subbands, which are also referred to as tones, subcarriers, bins, and frequency channels. With OFDM, each subband is associated with a respective subcarrier that may be modulated with data. 
     The broadcast transmission techniques described herein may be used for various types of broadcast data. For example, these techniques may be used for broadcast services that continually broadcast data (e.g., video, audio, news, and so on) to user terminals. These techniques may also be used for overhead channels (e.g., broadcast, paging, and control channels) in a wireless communication system. 
     1. MIMO Broadcast 
       FIG. 1  shows a MIMO system  100  with an access point (AP)  110  and user terminals (UTs)  120 . An access point is generally a fixed station that communicates with the user terminals and may also be referred to as a base station or some other terminology. A user terminal may be fixed or mobile and may also be referred to as a mobile station, a wireless device, or some other terminology. Access point  110  is equipped with multiple (Nap) antennas for data transmission. Each user terminal  120  is equipped with multiple (Nut) antennas for data reception. In general, the user terminals in the system may be equipped with the same or different numbers of antennas. For simplicity, the following description assumes that the user terminals in the MIMO system are equipped with the same number of antennas. For a centralized architecture, system controller  130  provides coordination and control for the access points. 
     For a single-carrier MIMO system, a MIMO channel formed by the Nap antennas at the access point and the Nut antennas at a given user terminal u may be characterized by an N ut ×N ap  channel response matrix  H   u , which may be expressed as: 
                         H   _     u     =     [           h     1   ,   1             h     1   ,   2           …         h     1   ,     N   ap                   h     2   ,   1             h     2   ,   2           …         h     2   ,     N   ap                 ⋮       ⋮       ⋰       ⋮             h       N   ut     ,   1             h       N   ut     ,   2           …         h       N   ut     ,     N   ap               ]       ,           Eq   ⁢           ⁢     (   1   )                 
where entry h i,j , for i=1 . . . N ut  and j=1 . . . N ap , denotes the coupling or complex gain between access point antenna j and user terminal antenna i.
 
As shown in  FIG. 1 , the user terminals may be distributed throughout the coverage area of the access point. A different MIMO channel is formed by the Nap antennas at the access point and the Nut antennas at each user terminal.
 
     Data may be transmitted in various manners in the single-carrier MIMO system. In one simple transmission scheme, one data symbol stream is transmitted from each access point antenna, and N S  data symbol streams are transmitted simultaneously from N S  of the N ap  access point antennas, where N S  is the number of spatial channels and N S ≦min {N ap , N ut }. The received symbols at user terminal u for this transmission scheme may be expressed as:
 
   r     u   = H     u     s + n     u ,  Eq (2)
 
where  s  is an N ap ×1 vector with N S  non-zero entries for N S  data symbols to be transmitted simultaneously by the access point;
           r   u  is an N ut ×1 vector with entries for Nut received symbols obtained via the Nut antennas at user terminal u; and     n   u  is a noise vector observed at user terminal u.
 
For simplicity, the noise is assumed to be additive white Gaussian noise (AWGN) with a zero mean vector and a covariance matrix of  Λ   u =σ u   2   I , where σ u   2  is the variance of the noise observed by user terminal u and  I  is the identity matrix.
       

     The N S  data symbol streams transmitted from the N ap  access point antennas interfere with each other at user terminal u. A given data symbol stream transmitted from one access point antenna may be received by all N ut  user terminal antennas at different amplitudes and phases. Each received symbol stream includes a component of each of the N S  transmitted data symbol streams. The N ut  received symbol streams would collectively include all of the N S  data symbol streams. However, these N S  data symbol streams are dispersed among the N ut  received symbol streams. User terminal u performs receiver spatial processing on the N ut  received symbol streams to recover the N S  data symbol streams transmitted by the access point. 
     The performance that can be achieved for user terminal u is dependent (to a large extent) on its channel response matrix  H   u . If a high degree of correlation exists within  H   u , then each data symbol stream would observe a large amount of interference from the other streams, which cannot be removed by the receiver spatial processing at the user terminal. The high level of interference degrades the SNR of each affected data symbol stream, possibly to a point where the data symbol stream cannot be decoded correctly by the user terminal. 
     For a data transmission to a specific user terminal via a given MIMO channel, system capacity may be achieved if the access point is provided with sufficient channel state information regarding the MIMO channel. The access point may then use this information to process data in a manner to maximize the throughput for the user terminal (e.g., select the proper rate for each data stream). Since different user terminals observe different MIMO channels, the access point would typically need to process data differently for each user terminal to maximize the throughput for that user terminal. 
     For a broadcast transmission, the access point transmits the same data to a number of user terminals within a broadcast coverage area. For broadcast, the access point typically does not have channel state information for the user terminals. Moreover, it is typically not practical to process data intended for multiple user terminals based on channel state information for a specific user terminal. 
     The broadcast transmission from the access point observes an ensemble of MIMO channels for different user terminals in the broadcast coverage area. A certain percentage of the MIMO channels may be considered as “bad”. For example, a bad channel can occur when the channel response matrix  H  exhibits a high degree of correlation, or when there is insufficient scattering, multipath (large coherence bandwidth), or temporal fading (large coherence time) in the channel. The occurrence of “bad” channels is random, and it is desirable to minimize the percentage of time this can occur for each user terminal. 
     For broadcast, the access point needs to transmit each data symbol stream at a sufficiently low rate so that the stream can be recovered by the user terminals even under the worst-case channel condition. Broadcast performance is then dictated by the expected worst-case channel condition for all of the user terminals in the coverage area. 
     A. MIMO Broadcast Transmission 
     Spatial spreading may be used to randomize an effective MIMO channel observed by each user terminal so that broadcast performance is not dictated by a single channel realization over a code block. With spatial spreading, the access point performs spatial processing on each code block with multiple steering matrices to effectively randomize the MIMO channel for each user terminal. Consequently, each user terminal observes an ensemble of channels across each code block and is not stuck on a single channel for an extended portion of the code block. 
     The spatial processing at the access point for spatial spreading in the MIMO system may be expressed as:
 
   x     mimo ( m )=   V   ( m )·   s   ( m ),  Eq (3)
 
where  s (m) is an N S ×1 vector with N S  data symbols to be sent in transmission span m;
           V (m) is an N ap ×N S  steering matrix for transmission span m; and     x   mimo (m) is an N   ap ×1 vector with N ap  transmit symbols to be sent from the N ap  access point antennas in transmission span m.
 
A transmission span may cover time and/or frequency dimensions. For example, in a single-carrier MIMO system, a transmission span may correspond to one symbol period, which is the time duration to transmit one data symbol. As another example, in a multi-carrier MIMO system, such as a MIMO system that utilizes OFDM, a transmission span may correspond to one subband in one OFDM symbol period. A transmission span may also cover multiple symbol periods and/or multiple subbands. Thus, m may be an index for time and/or frequency. A transmission span may also be referred to as a transmission interval, a signaling interval, a slot, and so on.
       

     A set of L steering matrices may be generated as described below and used for spatial spreading. This steering matrix set is denoted as { V }, or  V (i) for i=1 . . . L, where L may be any integer greater than one. One steering matrix in the set may be selected for each transmission span m and used for spatial processing by the access point for that transmission span. The results of the spatial processing are Nap transmit symbol streams for broadcast from the Nap access point antennas. 
     The received symbols at each user terminal with spatial spreading may be expressed as:
 
   r   ( m )=   H   ( m )·   V   ( m )·   s   ( m )+   n   ( m )=   H     eff ( m )·   s   ( m )+   n   ( m ),  Eq (4)
 
where  r (m) is an N ut ×1 vector with N ut  received symbols for transmission span m;
           H (m) is an N ut ×N ap  channel response matrix for transmission span m;     H   eff (m) is an N ut ×N S  effective channel response matrix for transmission span m, which is  H   eff (m)= H (m)· V (m); and     n (m) is a noise vector for transmission span m.
 
For simplicity, the channel response  H (m) is assumed to be constant over each transmission span. The quantities  H (m),  H   eff (m),  r (m) and  n (m) are different for different user terminals, whereas the quantities  V (m) and  s (m) are the same for all user terminals. To simplify notation, the subscript “u” for user terminal u is omitted from the user-specific quantities in equation (4) and in the following description.
       

     As shown in equation (4), because of the spatial spreading performed by the access point, the NS data symbol streams observe the effective channel response  H   eff (m) instead of the actual channel response  H (m) for each user terminal. If multiple steering matrices are used for broadcast transmission, then each data symbol stream effectively observes an ensemble of spatial channels of  H (m). Furthermore, if multiple steering matrices are used across a code block, then the data symbols in the code block would observe different channels across the code block. 
     In general, the access point may broadcast any number of (ND) data streams simultaneously to the user terminals, where N S ≧N D ≧1. For example, if N D =N S , then the access point may broadcast one data stream on each spatial channel of  H   eff (m). The maximum number of data streams that may be broadcast simultaneously is determined by the number of spatial channels for all user terminals, which in turn is determined by (1) the number of antennas at the access point and (2) the minimum number of antennas at all of the user terminals. If all user terminals are equipped with the same number of antennas, then min {N ap , N ut }≧N S &gt;N D . If N D =1 then the access point may broadcast one data stream from its Nap antennas. 
       FIG. 2  shows a process  200  for broadcasting data with spatial spreading. Initially, the access point processes data for ND data streams to obtain a set of ND data symbol blocks, one block for each data stream (block  212 ). Each data symbol block contains data symbols generated from one block of coded data, which may be called a code block or a coded data packet. The data processing may be performed as described below. The access point then partitions the ND data symbol blocks into NM data symbol subblocks to be broadcast in NM transmission spans, one subblock in each transmission span (block  214 ). NM is also referred to as the block length and is greater than one, or N M &gt;1. Each subblock may contain one or more data symbols from each of the ND blocks. For example, if N D =N S , then each subblock may contain NS data symbols from NS blocks for NS data streams. As another example, if N D =1, then each subblock may contain NS data symbols from one block for one data stream. The index m used to denote the transmission span for the current set of data symbol blocks is set to 1 (block  216 ). 
     For each transmission span m, the access point selects one steering matrix, which is denoted as  V (m), e.g., from the set of L steering matrices (block  218 ). The access point then performs spatial processing on data symbol subblock m with the steering matrix  V (m) to obtain transmit symbols (block  220 ). If transmission span m covers one data symbol vector, then the access point forms one vector  s (m) with up to NS data symbols from data symbol subblock m and spatially processes the vector  s (m) with the matrix  V (m) to obtain the transmit symbol vector  x   mimo (m), as shown in equation (3). If transmission span m covers multiple (NV) data symbol vectors, then the access point forms NV vectors  s   l (m), for l=1 . . . N V , from data symbol subblock m and spatially processes each vector  s   l (m) with the same steering matrix  V (m) to obtain a corresponding transmit symbol vector  x   mimo,l (m). In any case, the access point uses the same steering matrix  V (m) for spatial processing for all data symbol vectors in transmission span m. The access point further processes and broadcasts the resultant transmit symbol vectors via the Nap transmit antennas in transmission span m (block  222 ). 
     A determination is then made whether all NM data symbol subblocks have been processed and transmitted (i.e., whether m=N M ) (block  224 ). If the answer is ‘No’, then the index m is incremented for the next subblock/transmission span (block  226 ), and the process returns to block  218 . If the answer is ‘Yes’ for block  224 , then a determination is made whether there is more data to broadcast (block  228 ). If the answer is ‘Yes’, then the process returns to block  212  to start the processing for the next set of data symbol blocks. Otherwise, the process terminates. 
     Each set of data symbol blocks is thus spatially processed with NM steering matrices to obtain Nap transmit symbol sequences. Each transmit symbol sequence is broadcast from one antenna in NM transmission spans. The NM steering matrices randomize the effective MIMO channel observed by each user terminal for the ND data symbol blocks. The randomization of the MIMO channel results from using different steering matrices and not necessarily from randomness in the elements of the steering matrices. 
     As noted above, a transmission span may be defined to cover one or more symbol periods and/or one or more subbands. For improved performance, it is desirable to select the transmission span to be as small as possible so that (1) more steering matrices can be used for each data symbol block and (2) each user terminal can obtain as many “looks” of the MIMO channel as possible for each data symbol block. The transmission span should also be shorter than the coherence time of the MIMO channel, which is the time duration over which the MIMO channel can be assumed to be approximately static. Similarly, the transmission span should be smaller than the coherence bandwidth of the MIMO channel for a wideband system (e.g., an OFDM system). 
     B. MIMO Broadcast Reception 
       FIG. 3  shows a process  300  for receiving a broadcast transmission with spatial spreading by a given user terminal. Initially, the index m used to denote the transmission span for the current set of data symbol blocks is set to 1 (block  312 ). The user terminal obtains received data symbols from the Nut receive antennas for data symbol subblock m (block  314 ). The user terminal determines the steering matrix  V (m) used by the access point for subblock m (block  316 ) and uses  V (m) to derive  Ĥ   eff (m), which is an estimate of the channel response of the effective MIMO channel observed by the user terminal for subblock m (block  318 ). In the following description, “^” over a matrix, a vector, or a scalar denotes an estimate of the actual matrix, vector, or scalar. The user terminal then performs receiver spatial processing on the received data symbols with the effective channel response estimate  Ĥ   eff (m) and obtains detected symbols (or data symbol estimates) for subblock m (block  320 ). 
     A determination is then made whether all NM data symbol subblocks for the current data symbol block set have been received (i.e., whether m=N M ) (block  322 ). If the answer is ‘No’, then the index m is incremented for the next subblock/transmission span (block  324 ), and the process returns to block  314 . If the answer is ‘Yes’ for block  322 , then the user terminal processes (e.g., demodulates, deinterleaves, and decodes) the detected symbols for all NM subblocks to obtain decoded data for the current data symbol block set (block  326 ). A determination is then made whether there is more data to receive (block  328 ). If the answer is ‘Yes’, then the process returns to block  312  to start receiving the next set of data symbol blocks. Otherwise, the process terminates. 
     Each user terminal can derive estimates of the transmitted data symbols using various receiver processing techniques. These techniques include a channel correlation matrix inversion (CCMI) technique (which is also commonly referred to as a zero-forcing technique), a minimum mean square error (MMSE) technique, a successive interference cancellation (SIC) technique, and so on. In the following description, one data symbol stream is broadcast on each spatial channel of  H   eff (m). 
     For the CCMI technique, the user terminal derives a spatial filter matrix  M   ccmi (m) for each transmission span m based on the effective channel response estimate  Ĥ   eff (m) as follows:
 
   M     ccmi ( m )=[   Ĥ     eff   H ( m )·   Ĥ     eff ( m )] −1   · Ĥ     eff ( m )= R   −1 ( m )·   Ĥ     eff   H ( m ),  Eq (5)
 
where “ H ” denotes the conjugate transpose.
 
The user terminal can estimate the channel response matrix, e.g., based on received pilot symbols. A pilot symbol is a modulation symbol for pilot, which is data that is known a priori by both the access point and the user terminals. The user terminal may then compute the estimated effective channel response matrix as  Ĥ   eff (m)= Ĥ (m)· V (m). Alternatively, the user terminal can directly estimate the effective channel response matrix, e.g., based on received pilot symbols that have been transmitted using  V (m).
 
     The user terminal performs CCMI spatial processing as follows: 
                                   s   _     ^     ccmi     ⁡     (   m   )       =       ⁢           M   _     ccmi     ⁡     (   m   )       ·       r   _     ⁡     (   m   )           ,                 =       ⁢         R   _       -   1       ⁡     (   m   )         ⁣       ·           H   _     ^     eff   H     ⁡     (   m   )       ·     [             H   _     eff     ⁡     (   m   )       ·       s   _     ⁡     (   m   )         +       n   _     ⁡     (   m   )         ]       ,                   =       ⁢         s   _     ⁡     (   k   )       +         n   _     ccmi     ⁡     (   m   )           ,                 Eq   ⁢           ⁢     (   6   )                 
where  ŝ   ccmi (m) is an N S ×1 vector with detected symbols for transmission span m; and
           {circumflex over (n)}   ccmi (m)= M   ccmi (m)· n (m) is the CCMI filtered noise for transmission span m.       

     The SNR for the CCMI technique may be expressed as: 
                         γ     ccmi   ,   ℓ       ⁡     (   m   )       =         P   ℓ     ⁡     (   m   )             r   ℓℓ     ⁡     (   m   )       ⁢     σ   n   2           ,       for   ⁢           ⁢   ℓ     =     1   ⁢           ⁢   …   ⁢           ⁢     N   S         ,           Eq   ⁢           ⁢     (   7   )                 
where P l (m) is the transmit power for data symbol stream {s l } in transmission span m;
         r ll (m) is the l-th diagonal element of  R   −1 (m);   σ n   2  is the variance of the noise at the user terminal; and   γ ccmi,l (m) is the SNR of data symbol stream {s l } in transmission span m.
 
The quantity P l (m)/σ n   2  is the SNR of data symbol stream {s l } at the user terminal prior to the receiver spatial processing and is commonly referred to as the received SNR, the operating SNR, or the link margin. The quantity γ ccmi,l (m) is the SNR of data symbol stream {s l } after the receiver spatial processing and is also referred to as the post-detection SNR. In the following description, “SNR” refers to post-detection SNR unless noted otherwise. Due to the structure of  R (m), the CCMI technique may amplify the noise.
       

     For the MMSE technique, the user terminal derives a spatial filter matrix  M   mmse (m) for each transmission span m based on the effective channel response estimate  Ĥ   eff (m), as follows: 
                                 M   _     mmse     ⁡     (   m   )       =       ⁢         [               H   _     ^     eff   H     ⁡     (   m   )       ·           H   _     ^     eff     ⁡     (   m   )         +         φ   _     nn     ⁡     (   m   )         ]       -   1       ·           H   _     ^     eff   H     ⁡     (   m   )           ,                 =       ⁢         [               H   _     ^     eff   H     ⁡     (   m   )       ·           H   _     ^     eff     ⁡     (   m   )         +       σ   n   2     ⁢     I   _         ]       -   1       ·           H   _     ^     eff   H     ⁡     (   m   )           ,                 Eq   ⁢           ⁢     (   8   )                 
where  φ   nn (m) is an autocovariance matrix of the noise vector n(m), which is
           φ   nn (m)=E[ n (m)· n   H (m)], where E[x] is the expected value of x.
 
The second equality in equation (8) assumes that the noise vector  n (m) is AWGN with zero mean and variance of σ n   2 . The spatial filter matrix  M   mmse (m) minimizes the mean square error between the symbol estimates from the spatial filter and the data symbols.
       

     The user terminal performs MMSE spatial processing as follows: 
                                   s   _     ^     mmse     ⁡     (   m   )       =       ⁢           D   _     Q     ⁡     (   m   )       ·         M   _     mmse     ⁡     (   m   )       ·       r   _     ⁡     (   m   )           ,                 =       ⁢           D   _     Q     ⁡     (   m   )       ·         M   _     mmse     ⁡     (   m   )       ·     [             H   _     eff     ⁡     (   m   )       ·       s   _     ⁡     (   m   )         +       n   _     ⁡     (   m   )         ]         ,                 =       ⁢             D   _     Q     ⁡     (   m   )       ·       Q   _     ⁡     (   m   )       ·       s   _     ⁡     (   m   )         +         n   _     mmse     ⁡     (   m   )           ,                 Eq   ⁢           ⁢     (   9   )                 
where  ŝ   mmse (m) is an N S ×1 vector with detected symbols for transmission span m;
           Q (m)= M   mmse (m)· H   eff (m);     D   Q (m) is a diagonal matrix whose diagonal elements are the diagonal elements of  Q   −1 (m), or  D   Q (m)=[diag[ Q (m)]] −1 ; and     n   mmse (m)= D   Q (m)· M   mmse (m)· n (m) is the MMSE filtered noise.
 
The symbol estimates from the spatial filter are unnormalized estimates of the data symbols. The multiplication with the scaling matrix D Q (m) provides normalized estimates of the data symbols.
       

     The SNR for the MMSE technique may be expressed as: 
                         γ     mmse   ,   ℓ       ⁡     (   m   )       =           q   ℓℓ     ⁡     (   m   )         1   -       q   ℓℓ     ⁡     (   m   )           ⁢       P   ℓ     ⁡     (   m   )           ,       for   ⁢           ⁢   ℓ     =     1   ⁢           ⁢   …   ⁢           ⁢     N   S         ,           Eq   ⁢           ⁢     (   10   )                 
where q ll (m) is the l-th diagonal element of  Q (m); and
         γ mmse,l (m) is the SNR for data symbol stream {s l } in transmission span m.       

     For the SIC technique, the user terminal processes the Nut received symbol streams in ND successive stages for the ND data streams. For each stage, the user terminal performs spatial processing on either the Nut received symbol streams or Nut modified symbol streams from the preceding stage (e.g., using the CCMI, MMSE, or some other technique) to obtain one detected symbol stream. The user terminal then processes (e.g., demodulates, deinterleaves, and decodes) this detected symbol stream to obtain a corresponding decoded data stream. The user terminal next estimates and cancels the interference due to this stream and obtains Nut modified symbol streams for the next stage. The user terminal then repeats the same processing on the Nut modified symbol streams to recover another data stream. If the interference due to each data stream can be accurately estimated and canceled, then later recovered data streams experience less interference and in general are able to achieve higher SNRs on average. This permits the MIMO broadcast to employ higher data rates on those streams that are detected later, effectively improving the throughput of the broadcast. If different data rates are employed on different transmitted data streams, then the user terminals may decode these streams in a predetermined order from the lowest data rate stream to the highest data rate stream. 
     For the SIC technique, improved performance can be achieved by estimating the interference using decoded data instead of the detected symbols. In this case, the ND data symbol blocks for each block length are recovered one block at a time. Each data symbol block is detected and decoded in one stage, and the decoded data is used to estimate and cancel the interference due to the data symbol block. 
     For clarity, the following description assumes that (1) N D =N S  and each data symbol block/stream is transmitted as one entry of the data symbol vector  s (m) and (2) the ND data symbol streams are recovered in sequential order so that data symbol stream {s l } is recovered in stage l, for l=1 . . . N S . For the SIC technique, the input (received or modified) symbol streams for stage l, where l=1 . . . N S , may be expressed as:
 
   r     sic   l ( m )=   H     eff   l ( m )·   s     l ( m )+   n     l ( m ),  Eq (11)
 
where  r   sic   l (m) is a vector of N ut  modified symbols for transmission span m in stage l, and  r   sic   l (m)= r (m) for the first stage;
           s   l (m) is a vector of N S −l+1 data symbols not yet recovered for transmission span m in stage l;     H   eff   l (m) is an N ut ×(N ap −l+1) reduced effective channel response matrix for transmission span m in stage l; and     n   l (m) is a reduced vector of  n (m).       

     Equation (11) assumes that the data symbol streams recovered in the l−1 prior stages are canceled. The dimensionality of the matrix  H   eff (m) successively reduces by one column for each stage as a data symbol stream is recovered and canceled. For stage l, the reduced effective channel response matrix a  H   eff   l (m) is obtained by removing l−1 columns in the original matrix  H   eff (m) corresponding to the l−1 data symbol streams previously recovered, or  H   eff   l (m)=[ h   eff,l (m) h   eff,l+1 (m) . . .  h   eff,N     S   (m)], where  h   eff,l (m) is an N ut ×1 vector for the effective channel response observed by data symbol stream {s l } in transmission span m. 
     For stage l, the user terminal derives a spatial filter matrix  M   sic   l (m) based on the reduced effective channel response estimate  Ĥ   eff   l (m) (instead of the original effective channel response estimate  Ĥ   eff   l (m)) using the CCMI technique as shown in equation (5), the MMSE technique as shown in equation (8), or some other technique. The spatial filter matrix  M   sic   l (m) has dimensionality of (N S −l+1)×N ut . Since  Ĥ   eff   l (m) is different for each stage, the matrix  M   sic   l (m) is also different for each stage. 
     The user terminal performs spatial processing for stage l, as follows: 
                                   s   _     ^     sic   ℓ     ⁡     (   m   )       =       ⁢           D   _     sic   ℓ     ⁡     (   m   )       ·         M   _     sic   ℓ     ⁡     (   m   )       ·         r   _     sic   ℓ     ⁡     (   m   )           ,                 =       ⁢           D   _     sic   ℓ     ⁡     (   m   )       ·           ⁢         M   _     sic   ℓ     ⁡     (   m   )       ·     [             H   _     eff   ℓ     ⁡     (   m   )       ·         s   _     ℓ     ⁡     (   m   )         +         n   _     ℓ     ⁡     (   m   )         ]         ,                 =       ⁢             D   _     sic   ℓ     ⁡     (   m   )       ·         Q   _     sic   ℓ     ⁡     (   m   )       ·         s   _     ℓ     ⁡     (   m   )         +         n   _     sic   ℓ     ⁡     (   m   )           ,                 Eq   ⁢           ⁢     (   12   )                 
where  ŝ   sic   l (m) is a vector with N S −l+1 detected symbols for transmission span m in stage l;
           Q   sic   l (m)= M   sic   l (m)· H   eff   l (m);     D   sic   l (m) is a matrix of diagonal elements of [ Q   sic   l (m)] −1 ; and     n   sic   l (m) is the filtered noise for transmission span m in stage l.
 
The user terminal selects one of the detected symbol streams for recovery.
       

     Since only one data symbol stream is recovered in each stage, the user terminal can simply derive a 1×N ut  spatial filter row vector  m   l (m) for data symbol stream {s l } to be recovered in stage l. The row vector  m   l ( ) is one row of the matrix  M   sic   l (m). In this case, the spatial processing for stage l may be expressed as:
 
 ŝ   l ( m )=α l   · m     l ( m )·   r     sic   l ( m )=α l   · q     l ( m )·   s     l ( m )+ n   l ( m ),  Eq (13)
 
where  q   l (k) is the row of  Q   sic   l (m) corresponding to data symbol stream {s l } and α l  is a scaling factor for data symbol stream {s l }.
 
     In any case, the user terminal processes (e.g., demodulates, deinterleaves, and decodes) the detected symbol stream {ŝ l } to obtain a decoded data stream {{circumflex over (d)} l }. The user terminal also forms an estimate of the interference this stream causes to the other data symbol streams not yet recovered. To estimate the interference, the user terminal re-encodes, interleaves, and symbol maps the decoded data stream {{circumflex over (d)} l } in the same manner as performed at the access point and obtains a stream of “remodulated” symbols {{hacek over (s)} l }, which is an estimate of the data symbol stream {s l } just recovered. The user terminal then convolves the remodulated symbol stream {{hacek over (s)} l } with each of Nut elements in the effective channel response vector  h   eff,l (m) for stream {s l } to obtain Nut interference components  i   l (m) caused by this stream. The Nut interference components are then subtracted from the Nut modified symbol streams  r   sic   l (m) for stage l to obtain Nut modified symbol streams  r   sic,u   l+1 (m) for the next stage, or  r   sic   l+1 (m)= r   sic   l (m)− i   l (m). The modified symbol streams  r   sic   l+1 (m) represent the streams that would have been received if the data symbol stream {s l } had not been transmitted, assuming that the interference cancellation was effectively performed. 
     For the SIC technique, the SNR of each data symbol stream is dependent on (1) the spatial processing technique (e.g., CCMI or MMSE) used for each stage, (2) the specific stage in which the data symbol stream is recovered, and (3) the amount of interference due to the data symbol streams recovered in later stages. The SNR for the SIC technique with CCMI may be expressed as: 
                         γ       sic   ⁢     -     ⁢   ccmi     ,   ℓ       ⁡     (   m   )       =         P   ℓ     ⁡     (   m   )             r   ℓ     ⁡     (   m   )       ⁢     σ     n   ⁢             2           ,       for   ⁢           ⁢   ℓ     =     1   ⁢           ⁢   …   ⁢           ⁢     N   S         ,           Eq   ⁢           ⁢     (   14   )                 
where r l (m) is the diagonal element of [ R   l (m)] −1  for data symbol stream {s l }, and  R   l (m)=[ H   eff   l (m)] H · H   eff   l (m).
 
     The SNR for the SIC technique with MMSE may be expressed as: 
                         γ       sic   ⁢     -     ⁢   mmse     ,   ℓ       ⁡     (   m   )       =           q   ℓ     ⁡     (   m   )         1   -       q   ℓ     ⁡     (   m   )           ⁢       P   ℓ     ⁡     (   m   )           ,       for   ⁢           ⁢   ℓ     =     1   ⁢           ⁢   …   ⁢           ⁢     N   S         ,           Eq   ⁢           ⁢     (   15   )                 
where q l (m) is the diagonal element of  Q   sic   l (m) for data symbol stream {s l } where  Q   sic   l (m) is derived as shown for equation (9) but based on the reduced effective channel response matrix  Ĥ   eff   l (m) instead of the original effective channel response matrix  Ĥ   eff   l (m).
 
     In general, the SNR progressively improves for data symbol streams recovered in later stages because the interference from data symbol streams recovered in prior stages is canceled. This then allows higher rates to be used for data symbol streams recovered later. 
     The above description for the SIC technique assumes that each data symbol block is sent as one entry of  s (m). In general, each stage decodes and recovers one data symbol block, which may have been demultiplexed and sent in any number of entries of  s (m). The above description also assumes that the data streams are recovered in a sequential order determined by the stream index l. Better performance may be achieved by recovering the data streams in a sequential order determined by their required SNRs. For example, the data stream requiring the lowest SNR (e.g., the data stream sent with the lowest data rate and/or highest transmit power) may be recovered first, followed by the data stream with the next lowest required SNR, and so on. 
     C. Steering Matrix Selection 
     As noted above, a set of L steering matrices may be generated and used for spatial spreading. The steering matrices in the set may be selected for use in various manners. In one embodiment, the steering matrices are selected from the set in a deterministic manner. For example, the L steering matrices may be cycled through and selected in sequential order, starting with the first steering matrix  V (1), then the second steering matrix  V (2), and so on, and then the last steering matrix  V (L). In another embodiment, the steering matrices are selected from the set in a pseudo-random manner. For example, the steering matrix to use for each transmission span m may be selected based on a function f(m) that pseudo-randomly selects one of the L steering matrices, or steering matrix  V (f(m)). In yet another embodiment, the steering matrices are selected from the set in a “permutated” manner. For example, the L steering matrices may be cycled through and selected for use in sequential order. However, the starting steering matrix for each cycle may be selected in a pseudo-random manner, instead of always being the first steering matrix  V (1). The L steering matrices may also be selected in other manners, and this is within the scope of the invention. 
     The steering matrix selection may also be dependent on the number of steering matrices (L) in the set and the block length (NM). In general, the number of steering matrices may be greater than, equal to, or less than the block length. Steering matrix selection for these three cases may be performed as described below. 
     If L=N M , then the number of steering matrices matches the block length. In this case, a different steering matrix may be selected for each of the NM transmission spans used to broadcast a set of data symbol blocks. The NM steering matrices for the NM transmission spans may be selected in a deterministic, pseudo-random, or permutated manner, as described above. 
     If L&lt;N M , then the block length is longer than the number of steering matrices in the set. In this case, the steering matrices are reused for each data symbol block set and may be selected as described above. 
     If L&gt;N M , then a subset of the steering matrices is used for each data symbol block set. The selection of the specific subset to use for each data symbol block set may be deterministic or pseudo-random. For example, the first steering matrix to use for the current data symbol block set may be the steering matrix after the last one used for a prior data symbol block set. 
     D. MIMO System 
       FIG. 4  shows a block diagram of access point  110  and user terminal  120  in MIMO system  100 . User terminal  120  is one of the user terminals in  FIG. 1 . At access point  110 , a TX data processor  420  receives and processes (e.g., encodes, interleaves, and modulates) data for ND data streams and provides NS data symbol streams, where N S ≦N D ≦1. A TX spatial processor  430  receives and spatially processes the NS data symbol streams for spatial spreading, multiplexes in pilot symbols, and provides Nap transmit symbol streams to Nap transmitter units (TMTR)  432   a  through  432   ap . The processing by TX data processor  420  is described below, and the spatial processing by TX spatial processor  430  is as described above. Each transmitter unit  432  conditions (e.g., converts to analog, filters, amplifies, and frequency upconverts) a respective transmit symbol stream to generate a modulated signal. Nap transmitter units  432   a  through  432   ap  provide Nap modulated signals for transmission from Nap antennas  434   a  through  434   ap , respectively. 
     At user terminal  120 , Nut antennas  452   a  through  452   ut  receive the Nap transmitted signals, and each antenna  452  provides a received signal to a respective receiver unit (RCVR)  454 . Each receiver unit  454  performs processing complementary to that performed by transmitter unit  432  and provides (1) received data symbols to an RX spatial processor  460  and (2) received pilot symbols to a channel estimator  484  within a controller  480 . Receive spatial processor  460  performs spatial processing on Nut received symbol streams from Nut receiver units  454   a  through  454   ut  with spatial filter matrices from controller  480  and provides NS detected symbol streams, which are estimates of the NS data symbol streams broadcast by access point  110 . An RX data processor  470  then processes (e.g., demaps, deinterleaves, and decodes) the NS detected symbol streams and provides ND decoded data streams, which are estimates of the ND data streams. 
     Controllers  440  and  480  control the operation of various processing units at access point  110  and user terminal  120 , respectively. Memory units  442  and  482  store data and/or program codes used by controllers  440  and  480 , respectively. 
       FIG. 5A  shows a block diagram of a TX data processor  420   a  and a TX spatial processor  430   a , which are one embodiment of TX data processor  420  and TX spatial processor  430  at access point  110 . For this embodiment, TX data processor  420   a  includes ND TX data stream processors  520   a  through  520   nd  for ND data streams, {d l } for l=1 . . . N D . 
     Within each TX data stream processor  520 , an encoder  522  receives and encodes data stream {d l } based on a coding scheme and provides code bits. The data stream may carry one or more data packets, and each data packet is typically encoded separately to obtain a code block or coded data packet. The coding increases the reliability of the data transmission. The coding scheme may include cyclic redundancy check (CRC) generation, convolutional coding, Turbo coding, low density parity check (LDPC) coding, block coding, other coding, or a combination thereof. With spatial spreading, the SNR can vary across a code block even if the MIMO channel is static over the code block. A sufficiently powerful coding scheme may be used to combat the SNR variation across the code block, so that coded performance is proportional to the average SNR across the code block. Some exemplary coding schemes that can provide good performance for spatial spreading include Turbo code (e.g., the one defined by IS-856), LDPC code, and convolutional code. 
     A channel interleaver  524  interleaves (i.e., reorders) the code bits based on an interleaving scheme to achieve frequency, time and/or spatial diversity. The interleaving may be performed across a code block, a partial code block, multiple code blocks, one or more transmission spans, and so on. A symbol mapping unit  526  maps the interleaved bits based on a modulation scheme and provides a stream of data symbols {s l }. Unit  526  groups each set of B interleaved bits to form a B-bit value, where B≧1, and further maps each B-bit value to a specific modulation symbol based on the modulation scheme (e.g., QPSK, M-PSK, or M-QAM, where M=2 B ). Unit  526  provides a block of data symbols for each code block. 
     In  FIG. 5A , ND TX data stream processors  520   a  through  520   nd  process the ND data streams and provide ND data symbol blocks for each block length of NM transmission spans. One TX data stream processor  520  may also process the ND data streams, e.g., in a time division multiplex (TDM) manner. The same or different coding and modulation schemes may be used for the ND data streams. Furthermore, the same or different data rates may be used for the ND data streams. The data rate for each data stream is determined by the coding and modulation schemes used for that stream. 
     A multiplexer/demultiplexer (Mux/Demux)  528  receives and multiplexes/demultiplexes the data symbols for the ND data streams into NS data symbol streams. If N D =N S , then Mux/Demux  528  can simply provide the data symbols for each data stream as a respective data symbol stream. If N D =1, then Mux/Demux  528  demultiplexes the data symbols for the one data stream into NS data symbol streams. 
     TX spatial processor  430   a  receives ND data symbol blocks from TX data processor  420   a  and NM steering matrices  V (m) from controller  440  for each block length of NM transmission spans. The steering matrices may be retrieved from a steering matrix (SM) storage  542  within memory unit  442  or generated by controller  440  as they are needed. Within TX spatial processor  430   a , a matrix multiply unit  532  performs spatial processing on the data symbols for each transmission span m with the steering matrix  V (m) and provides transmit symbols for that transmission span. A multiplexer  534  multiplexes the transmit symbols with pilot symbols, e.g., in a time division multiplexed manner. For each transmission span, TX spatial processor  430   a  provides Nap transmit symbol sequences for broadcast from the Nap access point antennas in one or more symbol periods and/or on one or more subbands for that transmission span. TX spatial processor  430   a  further multiplexes the Nap transmit symbol sequences for different transmission spans and provides Nap transmit symbol streams, {x j } for j=1 . . . N ap , for the Nap access point antennas. 
       FIG. 5B  shows a block diagram of a TX data processor  420   b  and a TX spatial processor  430   b , which are another embodiment of TX data processor  420  and TX spatial processor  430  at access point  110 . For this embodiment, TX data processor  420   b  includes one TX data stream processor  520  for one data stream {d}. TX data stream processor  520  processes data stream {d} as described above for  FIG. 5A  and provides data symbols. A demultiplexer  529  demultiplexes the data symbols from processor  520  into NS data symbol streams, {s l } for l=1 . . . N S , so that each data symbol block is broadcast on NS spatial channels of  H (m). 
     Within TX spatial processor  430   b , a multiplexer  530  receives the NS data symbol streams from TX data processor  420   b , multiplexes in pilot symbols, and provides NS streams of data/pilot symbols. Matrix multiply unit  532  performs spatial processing on the data/pilot symbols for each transmission span m with the steering matrix  V (m) and provides transmit symbols for that transmission span. TX spatial processor  430   b  provides Nap transmit symbol streams, {x j } for j=1 . . . N ap , for the Nap access point antennas. TX spatial processor  430   b  performs spatial spreading on both pilot and data symbols, whereas TX spatial processor  430   a  performs spatial spreading on data symbols but not pilot symbols. 
       FIGS. 5A and 5B  show exemplary embodiments of TX data processor  420  and TX spatial processor  430  at access point  110 . Processors  420  and  430  may also be implemented in other manners, and this is within the scope of the invention. 
       FIG. 6A  shows a block diagram of an embodiment of the processing units at user terminal  120 , which may be used in conjunction with the access point embodiment shown in  FIG. 5A . Nut receiver units  454   a  through  454   ut  provide received pilot symbols, {r i   p } for =1 . . . N ut , to channel estimator  484 . If access point  110  transmits pilot symbols without spatial spreading (as shown in  FIG. 5A ), then channel estimator  484  derives  Ĥ (m), which is an estimate of the channel response matrix  H (m), based on the received pilot symbols. Channel estimator  484  then obtains the steering matrix  V (m) for each transmission span m and derives  Ĥ   eff (m), which is an estimate of the effective channel response matrix, as  Ĥ   eff (m)= H (m)· V (m). User terminal  120  is synchronized to access point  110  so that both entities use the same steering matrix  V (m) for each transmission span m. If access point  110  transmits pilot symbols with spatial spreading (as shown in  FIG. 5B ), then channel estimator  484  directly estimates the effective channel response matrix based on the received pilot symbols. In any case, channel estimator  484  provides the estimated effective channel response matrix  Ĥ   eff (m) for each transmission span. 
     Controller  480  derives a spatial filter matrix  M (m) and possibly a diagonal matrix  D (m) for each transmission span based on the estimated effective channel response matrix  Ĥ   eff (m) and using the CCMI, MMSE, or some other technique. RX spatial processor  460  obtains received data symbols, {r i   d } for i=1 . . . N ut , from receiver units  454   a  through  454   ut  and the matrices  M (m) and  D (m) from controller  480 . RX spatial processor  460  performs receiver spatial processing on the received data symbols for each transmission span with the matrices  M (m) and  D (m) and provides detected symbols to RX data processor  470 . 
     For the embodiment shown in  FIG. 6A , RX data processor  470   a  includes a multiplexer/demultiplexer  668  and ND RX data stream processors  670   a  through  670   nd  for the ND data streams. Mux/Demux  668  receives and multiplexes/demultiplexes the NS detected symbol streams for the NS spatial channels into ND detected symbol streams for the ND data streams. Within each RX data stream processor  670 , a symbol demapping unit  672  demodulates the detected symbols for the associated data stream in accordance with the modulation scheme used for that stream and provides demodulated data. A channel deinterleaver  674  deinterleaves the demodulated data in a manner complementary to the interleaving performed on that stream by access point  110 . A decoder  676  decodes the deinterleaved data in a manner complementary to the encoding performed by access point  110  on that stream. For example, a Turbo decoder or a Viterbi decoder may be used for decoder  676  if Turbo or convolutional coding, respectively, is performed by access point  110 . Decoder  676  provides a decoded data stream, which includes a decoded data packet for each data symbol block. 
       FIG. 6B  shows a block diagram of an RX spatial processor  460   b  and an RX data processor  470   b , which implement the SIC technique for user terminal  120 . RX spatial processor  460   b  and RX data processor  470   b  implement ND cascaded receiver processing stages for the ND data streams. For simplicity, N D =N S  and each data symbol stream corresponds to a respective data stream. Each of stages  1  to N D −1 includes a spatial processor  660 , an interference canceller  662 , an RX data stream processor  670 , and a TX data stream processor  680 . The last stage includes only a spatial processor  660   nd  and an RX data stream processor  670   nd . Each RX data stream processor  670  includes a symbol demapping unit, a channel deinterleaver, and a decoder, as shown in  FIG. 6A . Each TX data stream processor  680  includes an encoder, a channel interleaver, and a symbol mapping unit, as shown in  FIG. 5B . 
     For stage  1 , spatial processor  660   a  performs receiver spatial processing on the Nut received symbol streams and provides one detected symbol stream {ŝ 1 }. RX data stream processor  670   a  demodulates, deinterleaves, and decodes the detected symbol stream {ŝ 1 } and provides a corresponding decoded data stream {{circumflex over (d)} 1 }. TX data stream processor  680   a  encodes, interleaves, and modulates the decoded data stream {{circumflex over (d)} 1 } in the same manner performed by access point  110  for that stream and provides a remodulated symbol stream {{hacek over (s)} 1 }. Interference canceller  662   a  processes the remodulated symbol stream {{hacek over (s)} 1 } with the estimated effective channel response matrix  Ĥ   eff (m) to obtain Nut interference components due to data symbol stream {s 1 }. The Nut interference components are subtracted from the Nut received symbol streams to obtain Nut modified symbol streams, which are provided to stage  2 . 
     Each of stages  2  through N D −1 performs the same processing as stage  1 , albeit on the Nut modified symbol streams from the preceding stage instead of the Nut received symbol streams. The last stage performs spatial processing and decoding on the Nut modified symbol streams from stage N D −1 and does not perform interference estimation and cancellation. 
     Spatial processors  660   a  through  660   nd  may each implement the CCMI, MMSE, or some other technique. Each spatial processor  660  multiplies an input (received or modified) symbol vector  r   sic   l (m) with a spatial filter matrix  M   sic   l (m) to obtain a detected symbol vector  ŝ   sic   l (m) and provides the detected symbol stream for that stage. The matrix  M   sic   l (m) is derived based on the reduced effective channel response estimate  Ĥ   eff   l (m) for the stage. 
     2. MISO Broadcast 
       FIG. 7  shows a MISO system  700  with an access point  710  and user terminals  720 . Access point  710  is equipped with multiple (Nap) antennas for data transmission. Each user terminal  720  is equipped with a single antenna for data reception. The user terminals may be distributed throughout the coverage area of access point  710 . A different MISO channel is formed by the Nap antennas at the access point and the single antenna at each user terminal. The MISO channel for a given user terminal may be characterized by a 1×N ap  channel response row vector  h , which is  h =[h 1  h 2  . . . h N     ap   ], where entry h j , for j=1 . . . N ap , denotes the coupling between access point antenna j and the user terminal antenna. 
     Spatial spreading may be used to randomize the effective MISO channel observed by each single-antenna user terminal so that broadcast performance is not dictated by the expected worst-case channel condition. For the MISO system, the access point performs spatial processing with steering vectors, which are degenerated steering matrices containing just one column. 
     The spatial processing at the access point for spatial spreading in the MISO system may be expressed as:
 
   X     miso ( m )=   v   ( m )· s ( m ),  Eq (16)
 
where s(m) is a data symbol to be sent in transmission span m;
           v (m) is an N ap ×1 steering vector for transmission span m; and     x   miso (m) is an N ap ×1 vector with N ap  transmit symbols to be sent from the N ap  access point antennas in transmission span m.       

     A set of L steering vectors may be generated and is denoted as { v }, or  v (i) for i=1 . . . L. One steering vector in the set is selected for each transmission span m and used for spatial processing by the access point for that transmission span. 
     The received symbols at each single-antenna user terminal with spatial spreading may be expressed as:
 
 r ( m )=   h   ( m )·   v   ( m )· s ( m )+ n ( m )= h   eff ( m )· s ( m )+ n ( m ),  Eq (17)
 
where r(m) is a received symbol for transmission span m;
         h eff (m) is an effective channel response for transmission span m, which is h eff (m)= h (m)· v (m); and   n(m) is the noise for transmission span m.       

     As shown in equation (17), because of the spatial spreading performed by the access point, the data symbol stream broadcast by the access point observes the effective channel response h eff (m), which includes the actual channel response  h (m) and the steering vector  v (m). The user terminal may derive  ĥ (m), which is an estimate of the channel response vector  h (m) (e.g., based on received pilot symbols). The user terminal may then compute ĥ eff (m), which is an effective channel response estimate, as ĥ eff (m)= ĥ (m)· v (m). Alternatively, the user terminal can directly estimate the effective channel response, e.g., based on received pilot symbols that have been transmitted using  v (m). In any case, the user terminal can perform detection (e.g., matched filtering and/or equalization) on the received symbols r(m) with the effective channel response estimate ĥ eff (m) to obtain detected symbols ŝ(m). 
     Broadcast transmission and reception for the MISO system may be performed similarly to that described above for  FIGS. 2 and 3 . However, only one spatial channel is available and used for broadcast transmission in the MISO system. Referring to  FIG. 2 , for broadcast transmission in the MISO system, one data symbol block is generated (block  212 ) and partitioned into NM subblocks, which are to be broadcast in NM transmission spans (block  214 ). A steering vector is selected for each subblock/transmission span (block  218 ) and used for spatial processing for the data symbol(s) in the subblock (block  220 ). The transmit symbols for each subblock are broadcast via the Nap access point antennas in the associated transmission span (block  222 ). 
     Referring to  FIG. 3 , for broadcast reception in the MISO system, one or more received data symbols are obtained from the single antenna at the user terminal for each subblock (block  314 ). The steering vector used by the access point for each subblock is determined (block  316 ) and used to derive the effective channel response estimate ĥ eff (m) (block  318 ), which is then used for detection of the received data symbol(s) for the subblock (block  320 ). After all NM subblocks for the current data symbol block have been received, the detected symbols for the block are processed (demodulated, deinterleaved, and decoded) to obtain the decoded data for the block (block  326 ). 
       FIG. 8  shows a block diagram of access point  710  and user terminal  720  in MISO system  700 . User terminal  720  is one of the user terminals in  FIG. 7 . At access point  710 , a TX data processor  820  performs data processing on a data stream {d} to obtain a corresponding data symbol stream {s}. TX data processor  820  may be implemented with TX data stream processor  520  in  FIG. 5B . A TX spatial processor  830  performs spatial spreading on the data symbol stream with the steering vectors (e.g., as shown in equation (16)), multiplexes in pilot symbols, and provides Nap transmit symbol streams. Nap transmitter units  832   a  through  832   ap  condition the Nap transmit symbol streams to generate Nap modulated signals, which are transmitted from Nap antennas  834   a  through  834   ap , respectively. 
     At user terminal  720 , the Nap transmitted signals are received by an antenna  852 , and the received signal from the antenna is conditioned by a receiver unit  854  to obtain received symbols. A channel estimator  884  derives the effective channel response estimate ĥ eff (m) based on the received pilot symbols and the steering vector  v (m) used for each transmission span. A detector  860  performs detection (e.g., matched filtering and/or equalization) on the received data symbols with the effective channel response estimate ĥ eff (m) and provides a stream of detected symbols {ŝ}. An RX data processor  870  processes (e.g., demaps, deinterleaves, and decodes) the detected symbol stream and provides a decoded data stream {{circumflex over (d)}}. RX data processor  870  may be implemented with RX data stream processor  670   a  in  FIG. 6A . 
     Controllers  840  and  880  control the operation of various processing units at access point  710  and user terminal  720 , respectively. Memory units  842  and  882  store data and/or program codes used by controllers  840  and  880 , respectively. 
     3. OFDM-Based Systems 
     The broadcast transmission techniques described herein may be used for single-carrier as well as multi-carrier systems. Multiple carriers may be obtained with OFDM or some other construct. For an OFDM-based system, spatial spreading may be performed on each of the subbands used for broadcast. 
     For a MIMO system that utilizes OFDM (i.e., a MIMO-OFDM system), one data symbol vector  s (k,n) may be formed for each subband k in each OFDM symbol period n. Vector  s (k,n) contains up to NS data symbols for broadcast via the NS spatial channels of subband k in OFDM symbol period n. The index m for transmission span is substituted with k,n for subband k and OFDM symbol period n. Up to NF vectors,  s (k,n) for k=1 . . . N F , may be broadcast concurrently on the NF subbands in one OFDM symbol period. A transmission span may cover one or more subbands in one or more OFDM symbol periods. 
     The ND data symbol blocks may be broadcast in various manners in the MIMO-OFDM system. For example, each data symbol block may be broadcast as one entry of the vector  s (k,n) for each of the NF subbands. In this case, each data symbol block is broadcast on all NF subbands and achieves frequency diversity. Each data symbol block may further span one or multiple OFDM symbol periods. Each data symbol block may thus span frequency and/or time dimensions (by system design) plus spatial dimension (with spatial spreading). 
     The steering matrices may also be selected in various manners for the MIMO-OFDM system. The steering matrices for the subbands may be selected in a deterministic, pseudo-random, or permutated manner, as described above. For example, the L steering matrices in the set may be cycled through and selected in sequential order for subbands  1  through NF in OFDM symbol period n, then subbands  1  through NF in OFDM symbol period n+1, and so on. The number of steering matrices in the set may be less than, equal to, or greater than the number of subbands. The three cases described above for L=N M , L&lt;N M , and L&gt;N M  may also be applied for the subbands, with NM being replaced with NF. 
     For a MISO system that utilizes OFDM (i.e., a MISO-OFDM system), one data symbol s(k,n) may be broadcast on each subband k in OFDM symbol period n. Up to NF data symbols, s(k,n) for k=1 . . . N F , may be broadcast concurrently on the NF subbands in one OFDM symbol period. Each data symbol block may be broadcast on one or multiple subbands and/or in one or multiple OFDM symbol periods. The steering vectors may be selected in a manner similar to that for the steering matrices in the MIMO-OFDM system. 
     For an OFDM-based system, each transmitter unit  432  in  FIG. 4  and each transmitter unit  832  in  FIG. 8  perform OFDM modulation on the transmit symbols for all NF subbands of an associated transmit antenna. For OFDM modulation, the NF transmit symbols to be broadcast on the NF subbands in each OFDM symbol period are transformed to the time-domain using an NF-point inverse fast Fourier transform (IFFT) to obtain a “transformed” symbol that contains NF chips. To combat intersymbol interference (ISI), which is caused by frequency selective fading, a portion (or Ncp chips) of each transformed symbol is typically repeated to form a corresponding OFDM symbol. Each OFDM symbol is broadcast in one OFDM symbol period, which is N F +N cp  chip periods, where Ncp is the cyclic prefix length. Each transmitter unit generates a stream of OFDM symbols and further conditions the OFDM symbol stream to generate a modulated signal for broadcast from the associated antenna. Each receiver unit  454  in  FIG. 4  and each receiver unit  854  in  FIG. 8  perform the complementary OFDM demodulation on its received signal to obtain received data symbols and received pilot symbols. 
     4. Transmit Diversity 
     Spatial spreading may be used in combination with various transmit diversity schemes such as space-time transmit diversity (STTD), space-frequency transmit diversity (SFTD), orthogonal transmit diversity (OTD), and so on. STTD transmits each pair of data symbols from two antennas in two symbol periods to achieve space and time diversity. SFTD transmits each pair of data symbols from two antennas in two subbands to achieve space and frequency diversity. OTD transmits two data symbols simultaneously from two antennas in two symbol periods using two orthogonal codes to achieve space and time diversity. Spatial spreading may provide improved performance for these transmit diversity schemes. 
     For the STTD scheme, the access point generates two coded symbol vectors, e.g.,  s   1 (m)=[s a (m) s b (m)] and  s   2 (m)=[s b *(m)−s a *(m)] T , for each pair of data symbols s a (m) and s b (m) to be broadcast in transmission span m, where “*” denotes the complex conjugate and “T” denotes the transpose. Each vector includes two coded symbols that are to be broadcast from the Nap access point antennas in one symbol period. Vector  s   1 (m) is broadcast in the first symbol period, and vector  s   2 (m) is broadcast in the next symbol period. Each data symbol is included in both vectors and is thus broadcast over two symbol periods. 
     The access point performs spatial spreading on the two vectors  s   1 (m) and  s   2 (m) using the same steering matrix, as follows:
 
   x     sttd,i ( m )=   V     sttd ( m )·   s     i ( m ), for i=1, 2,  Eq (18)
 
where  V   sttd (m) is an N ap ×2 steering matrix for transmission span m; and
           x   sttd,i (m) is an N ap ×1 vector with N ap  transmit symbols to be sent from the N ap  access point antennas in symbol period i of transmission span m.       

     If the user terminal is equipped with a single antenna, then the received symbols may be expressed as:
 
 r   i ( m )=   h   ( m )·   V     sttd ( m )·   s     i ( m )+ n   i ( m )=   h     eff,sttd ( m )·   s     i ( m )+ n   i ( m ),  Eq (19)
 
where r i (m) is a received symbol for symbol period i of transmission span m;
           h (m) is an 1×N ap  channel response row vector for transmission span m;     h   eff,sttd (m) is a 1×2 effective channel response row vector for transmission span m, which is  h   eff,sttd (m)= h (m)· V   sttd (m)=[h eff,1 (m) h eff,2  (m)]; and   n i (m) is the noise for symbol period i of transmission span m.
 
The channel response h(m) is assumed to be constant over the two symbol periods of transmission span m.
       

     The single-antenna user terminal may derive estimates of the two data symbols, s a (m) and s b (m), as follows: 
                                 s   ^     a     ⁡     (   m   )       =       ⁢               h   ^       eff   ,   1     *     ⁡     (   m   )       ·       r   1     ⁡     (   m   )         -           h   ^       eff   ,   2       ⁡     (   m   )       ·       r   2   *     ⁡     (   m   )               β   ′     ⁡     (   m   )                       =       ⁢         s   a     ⁡     (   m   )       +       n   a   ′     ⁡     (   m   )           ,           ⁢   and           ⁢     
     ⁢                 s   ^     b     ⁡     (   m   )       =       ⁢               h   ^       eff   ,   2     *     ⁡     (   m   )       ·       r   1     ⁡     (   m   )         +           h   ^       eff   ,   1       ⁡     (   m   )       ·       r   2   *     ⁡     (   m   )               β   ′     ⁡     (   m   )                       =       ⁢         s   b     ⁡     (   m   )       +       n   b   ′     ⁡     (   m   )           ,                   Eq   ⁢           ⁢     (   20   )                 
where ĥ eff,i (m) is an estimate of h eff,i (m), for i=1, 2;
         β′(m)=|ĥ eff,1 (m)| 2 +|ĥ eff,2 (m)| 2 ; and   n a ′(m) and n b ′(m) are post-processed noise for detected symbols ŝ a (m) and ŝ b (m), respectively.       

     If the user terminal is equipped with multiple antennas, then the received symbols may be expressed as:
 
   r     i ( m )=   H   ( m )·   V     sttd ( m )·   s     i ( m )+   n     i ( m )=   H     eff,sttd ( m )·   s     i ( m )+   n     i ( m ),  Eq (21)
 
where  r   i (m) is an N ut ×1 vector with N ut  received symbols for symbol period i of transmission span m;
           H (m) is an N ut ×N ap  channel response matrix for transmission span m;     H   eff,sttd (m) is an N ut ×2 effective channel response matrix for transmission span m, which is  H   eff,sttd (m)= H (m)· V   sttd (m)=[ h   eff,1 (m)  h   eff,2 (m)]; and     n   i (m) is a noise vector for symbol period i of transmission span m.
 
The channel response H(m) is assumed to be constant over the two symbol periods of transmission span m.
       

     The multi-antenna user terminal may derive estimates of the two data symbols, s a (m) and s b (m), as follows: 
                               s   ^     a     ⁡     (   m   )       =                   h   _     ^       eff   ,   1     H     ⁡     (   m   )       ·         r   _     1     ⁡     (   m   )         -           r   _     2   H     ⁡     (   m   )       ·           h   ^     _       eff   ,   2       ⁡     (   m   )               β   ′′     ⁡     (   m   )         =         s   a     ⁡     (   m   )       +       n   a   ′′     ⁡     (   m   )             ,   and     ⁢     
     ⁢             s   ^     b     ⁡     (   m   )       =                   h   ^     _       eff   ,   2     H     ⁡     (   m   )       ·         r   _     1     ⁡     (   m   )         +           r   _     2   H     ⁡     (   m   )       ·           h   ^     _       eff   ,   1       ⁡     (   m   )               β   ′′     ⁡     (   m   )         =         s   b     ⁡     (   k   )       +       n   b   ′′     ⁡     (   m   )             ,       ⁢                   Eq   ⁢           ⁢     (   22   )                 
where  ĥ   eff,i (m) is an estimate of  h   eff,i (m), for i=1, 2;
         β*(m)=∥ ĥ   eff,1 (m)| 2 +∥ ĥ   eff,2 (m)∥ 2 ; and   n a *(m) and n b *(m) are post-processed noise for detected symbols ŝ a (m) and ŝ b (m), respectively.       

     For the SFTD scheme, the two vectors  s   1 (m) and  s   2 (m) are broadcast on two different subbands in the same symbol period. The same transmit and receive processing described above can be performed for the SFTD scheme, where the index i now denotes subband instead of symbol period. Since the channel response is assumed to be approximately constant over the transmission span, two adjacent subbands k and k+1 may be used to broadcast the two vectors  s   1 (m) and  s   2 (m). 
     5. Hybrid Multi-Antenna System 
       FIG. 9  shows a multi-antenna system  900  with an access point  910  and user terminals  920 . Access point  910  is equipped with multiple (Nap) antennas for data transmission. Each user terminal  920  may be equipped with a single antenna or multiple (Nut) antennas for data reception. Each multi-antenna user terminal has a respective MIMO channel with the access point and is able to receive MIMO and MISO broadcast transmissions from the access point. Each single-antenna user terminal has a respective MISO channel with the access point and is able to receive a MISO broadcast transmission and possibly a portion of a MIMO broadcast transmission from the access point, as described below. 
     Access point  910  may broadcast data in various manners in system  900 . In one embodiment, access point  910  sends (1) a MIMO broadcast transmission that can be received by multi-antenna user terminals and (2) a MISO broadcast transmission that can be received by both single-antenna and multi-antenna user terminals. The MIMO and MISO broadcast transmissions may be sent (1) in different time intervals using time division multiplexing (TDM), (2) on different disjoint sets of subbands using frequency division multiplexing (FDM), (3) on different code channels using code division multiplexing (CDM), some other multiplexing scheme, or any combination thereof. In another embodiment, access point  910  sends a MIMO broadcast transmission in a manner such that single-antenna user terminals can recover a portion of the broadcast transmission (e.g., for basic broadcast service) and multi-antenna user terminals can recover all of the broadcast transmission (if they have sufficient link margin). In yet another embodiment, access point  910  can adjust the broadcast transmission (e.g., between MIMO and MISO broadcasts) based on the expected channel conditions for the user terminals. 
     6. Broadcast Transmission Schemes 
     A multi-antenna system may perform MIMO broadcast in various manners. In a first MIMO broadcast scheme, the access point broadcasts multiple (ND) data streams simultaneously and uses the same data rate and the same transmit power for all data streams, where N S ≧N D &gt;1. The data rate may be selected, for example, based on the expected worst-case effective channel for the multi-antenna user terminals, which should be better than the expected worst-case actual channel for these user terminals. Most multi-antenna user terminals within the broadcast coverage area can then recover the ND data streams. 
     In a second MIMO broadcast scheme, the access point broadcasts ND data streams simultaneously and uses different data rates but the same transmit power for these streams. This broadcast scheme may be used to provide “tiered” broadcast services over the broadcast coverage area. Each data stream has a different broadcast coverage area determined by its data rate. The data stream with the lowest data rate has the largest broadcast coverage area, and the data stream with the highest data rate has the smallest broadcast coverage area. Each user terminal may be able to recover one, some, or all of the data streams depending on (1) its location and channel condition and (2) the receiver spatial processing technique employed. If a user terminal uses a linear receiver spatial processing technique (e.g., the CCMI or MMSE technique), then it can recover data streams with higher data rates if it has a sufficiently high link margin. The user terminal may be able to only recover data streams with lower data rates if it has a low link margin (e.g., is located at the edge of the coverage area). If the user terminal uses the SIC technique, then it may be able to recover data streams with higher data rates as well as data streams with lower data rates even if it is located at the edge of the coverage area. The user terminal can recover the lower rate data streams first and perform interference cancellation to achieve higher SNRs needed to recover the higher rate data streams. 
     In a third MIMO broadcast scheme, the access point broadcasts ND data streams simultaneously and uses the same data rate but different transmit powers for these streams. Different transmit powers may be obtained by multiplying the data symbols for each data stream with a scaling factor that determines the amount of transmit power for that data stream. Tiered broadcast services may also be achieved with this broadcast scheme. The data stream with the highest transmit power has the largest broadcast coverage area and can be recovered by the most user terminals. Conversely, the data stream with the lowest transmit power has the smallest broadcast coverage area. The lower power data streams may also be recovered by user terminals with low link margin if they use the SIC technique. 
     The second and third MIMO broadcast schemes may be used to support both multi-antenna user terminals and single-antenna user terminals. The single-antenna user terminals can recover the data stream with the lowest data rate or the highest transmit power. The remaining data streams would act as interference to this data stream. The multi-antenna user terminals can recover more data streams using the additional antennas. If a multi-antenna user terminal uses the SIC technique described above, then the data streams may be recovered in a sequential order determined by their required SNRs. The data stream with the lowest data rate or the highest transmit power is recovered first, followed by the data stream with the next lowest data rate or next highest transmit power, and so on. 
     In a fourth MIMO broadcast scheme, the access point transmits different numbers of data streams depending on the expected capacity of the wireless channels for the user terminals. Channel capacity is a function of the operating SNR as well as the channel characteristics (e.g., whether the channel gains for different transmit/receive antenna pairs are correlated). When the expected channel capacity is low, the access point can broadcast fewer data streams and distribute the available transmit power over these fewer streams so that each stream can achieve a higher SNR. Conversely, when the expected channel capacity is higher, the access point can broadcast more data streams. 
     For both MIMO and MISO broadcasts, the access point can adjust the data rate for each data stream based on various factors such as channel capacity, service requirements, and so on. Other broadcast schemes may also be implemented with spatial spreading, and this is within the scope of the invention. 
     7. Broadcast Performance 
     The performance of each data symbol stream is dependent on the diversity order achieved for that stream. The diversity order for each data symbol stream is, in turn, dependent on the number of transmit antennas, the number of receive antennas, the receiver spatial processing technique, and whether spatial spreading was used. In general, performance improves as diversity order increases. 
     Without spatial spreading, each of the NS data symbol streams observes the same diversity order when a linear receiver spatial processing technique (e.g., the CCMI or MMSE technique) is used to detect the data symbol streams. If N ut ≧N ap  and one data symbol stream is broadcast on each spatial channel of  H   eff (m) so that N D =N S =N ap , then each data symbol stream observes a diversity order of N ut −N ap +1. For a symmetric MIMO channel with N ap =N ut , each detected symbol stream has a diversity order of one and a Rayleigh distribution for its SNR. All of the data symbol streams have the same SNR distribution. 
     Without spatial spreading, each data symbol stream observes a different diversity order when the SIC technique is used to detect the NS data symbol streams. Again, if N ut ≧N ap  and one data symbol stream is broadcast on each spatial channel of  H   eff (m), then the diversity order for each data symbol stream is N ut −N ap +l, where l is the stage number in which the stream is detected. Thus, data symbol streams that are detected later have higher diversity order and tend to have better SNRs, which allow higher data rates to be used for these streams. 
     With spatial spreading, the diversity order for each data symbol stream is effectively improved by the use of multiple different steering matrices for each code block within the stream. Each different steering matrix allows the code block to obtain a different “look” of the MIMO channel, which may be equated to having a different transmit or receive antenna. The diversity order for each data symbol stream may then be related to the number of different steering matrices used for the code block, which can be much larger than the number of access point antennas and the number of user terminal antennas. Spatial spreading typically provides greater improvement for data symbol streams with lower diversity orders. 
     Spatial spreading can be used to improve the throughput and/or the coverage area for a broadcast transmission. Conventional MIMO and MISO systems (without spatial spreading) typically select a data rate for broadcast transmission based on the expected worst-case channel condition for all user terminals in the broadcast coverage area. This worst-case channel condition typically corresponds to a “bad” channel that does not fade/change across an entire code block. With spatial spreading, the effective MIMO or MISO channel is randomized across each code block, and the likelihood of any user terminal observing a bad channel for the entire code block is substantially reduced. This then allows a higher data rate to be used for broadcast transmission. Equivalently, for a given data rate, spatial spreading can provide a larger broadcast coverage area. In general, a higher data rate for a broadcast transmission corresponds to a smaller broadcast coverage area. Furthermore, a more stringent outage requirement (or a lower outage probability) corresponds to a smaller broadcast coverage area. Spatial spreading can provide improved performance (e.g., higher data rate, larger broadcast coverage area, and/or lower outage probability) over the conventional MIMO and MISO systems. 
       FIG. 10A  shows plots of the cumulative distribution function (CDF) of the overall spectral efficiency achieved for an exemplary MIMO system. For this MIMO system, the access point is equipped with four antennas (N ap =4), the user terminals are randomly distributed throughout the coverage area, and each user terminal is equipped with four antennas (N ut= 4). The MIMO channels for the user terminals are assumed to be as described above for equation (1) and the operating SNR per receive antenna is 20 dB for user terminals located at the edge of coverage. The user terminals use the MMSE technique. 
     Plot  1010  shows the CDF of the overall spectral efficiency for the case in which spatial spreading is not performed for broadcast transmission, which is equivalent to performing transmit steering with a single steering matrix (L=1) all the time. Spectral efficiency is given in units of bits per second per Hertz (bps/Hz). For a given spectral efficiency x, the CDF indicates the percentage of user terminals achieving overall spectral efficiency worse than x. For example, point  1012  indicates that one percent ( 10   −2 ) of the user terminals achieve overall spectral efficiency worse than 9 bps/Hz. If the access point broadcasts data at an overall rate of 9 bps/Hz, then one percent of the user terminals will not be able to correctly decode the broadcast transmission. This percentage is also referred to as the outage probability. 
     Plots  1020 ,  1030  and  1040  show the CDFs of the overall spectral efficiency achieved with spatial spreading using 4, 16 and 64 steering matrices, respectively. Points  1022 ,  1032  and  1042  indicate that, for one percent outage probability, the overall spectral efficiency is 12.5, 14.6 and 15.8 bps/Hz with 4, 16 and 64 steering matrices, respectively. For one percent outage probability, the use of spatial spreading improves the overall spectral efficiency from 9 bps/Hz to approximately 15.8 bps/Hz (with 64 steering matrices) for the exemplary MIMO system. Line  1050  is for 50% outage probability and may be referenced to determine the average overall spectral efficiency for the four cases. 
       FIG. 10B  shows plots of the CDF of the overall spectral efficiency achieved for an exemplary MISO system. For this MISO system, the access point is equipped with four antennas (N ap =4), the user terminals are randomly distributed throughout the coverage area, and each user terminal is equipped with a single antenna (N ut =1). The MISO channels for the user terminals are assumed to be as described above and the operating SNR/Rx is 10 dB for user terminals located at the edge of coverage. 
     Plot  1060  shows the CDF of the overall spectral efficiency for the case in which spatial spreading is not performed (L=1) for broadcast transmission. Plots  1070 ,  1080  and  1090  show the CDFs of the overall spectral efficiency achieved with spatial spreading using 4, 16 and 64 steering matrices, respectively. Points  1062 ,  1072 ,  1082 , and  1092  indicate that, for one percent outage probability, the overall spectral efficiency is 0.1, 0.8, 1.7, and 2.2 bps/Hz with 1, 4, 16 and 64 steering matrices, respectively. Again, substantial gain is achieved by the use of spatial spreading for broadcast transmission. 
       FIGS. 10A and 10B  show the performance for exemplary MIMO and MISO systems with some specific assumptions. In general, the amount of improvement may be dependent on various factors such as, for example, the characteristics of the wireless channels, the number of transmit and receive antennas, the spatial processing technique used at the user terminals, the coding and modulation schemes used for data transmission, and so on. 
     8. Steering Matrix and Vector Generation 
     The steering matrices used for spatial spreading in the MIMO system and the steering vectors used for the MISO system may be generated in various manners. Some exemplary schemes for generating these steering matrices and vectors are described below. The set of steering matrices/vectors may be pre-computed and stored at the access point and user terminals and thereafter retrieved for use as they are needed. Alternatively, these steering matrices/vectors may be computed in real time as they are needed. 
     A. Steering Matrix Generation 
     The steering matrices should be unitary matrices and satisfy the following condition:
 
   V     H ( i )·   V   ( i )=   I   , for  i= 1  . . . L.   Eq (23)
 
Equation (23) indicates that each column of  V (i) has unit energy and the columns of  V (i) are orthogonal to one another. This condition ensures that the N S  data symbols broadcast simultaneously using the steering matrix  V (i) have the same power and are orthogonal to one another prior to transmission.
 
     Some of the steering matrices may also be uncorrelated so that the correlation between any two uncorrelated steering matrices is zero or a low value. This condition may be expressed as:
 
   C   ( ij )=   V     H ( i )·   V   ( j )≈ 0 , for  i= 1  . . . L, j= 1  . . . L , and  i≠j,   Eq (24)
 
where  C (ij) is the correlation matrix for  V (i) and  V (j) and  0  is a matrix of all zeros. The condition in equation (24) may improve performance for some applications but is not necessary for most applications.
 
     A set of L steering matrices { V } may be generated using various schemes. In a first scheme, the L steering matrices are generated based on matrices of random variables. An N S ×N ap  matrix  G  with elements that are independent identically distributed (IID) complex Gaussian random variables, each having zero mean and unit variance, is initially generated. An N ap ×N ap  correlation matrix of  G  is computed as  R = G   H · G  and decomposed using eigenvalue decomposition as:
 
   R = E · D · E     H ,  Eq (25)
 
where  E  is an N ap ×N S  unitary matrix of eigenvectors of  R ; and
           D  is an N S ×N S  diagonal matrix of eigenvalues of  R .
 
The diagonal matrix  D  contains eigenvalues of  R , which represent the power gains for the N S  eigenmodes of  G . The matrix  E  is used as a steering matrix  V (i) and added to the set. The steering matrix  V (i) is a unitary matrix because the matrix  E  is obtained through eigenvalue decomposition. The process is repeated until all L steering matrices are generated.
       

     In a second scheme, the L steering matrices are generated based on a set of (log 2  L)+1 independent isotropically distributed unitary matrices. A random unitary matrix is isotropically distributed if its probability density is unchanged by pre-multiplication by any deterministic N ap ×N ap  unitary matrix. The index i for the steering matrices in the set may be denoted as i=l 1 l 2  . . . l Q , where Q=log 2  L, l 1  is the first bit of index i, l Q  is the last bit of index i, and each bit can take on a value of either 0 or 1. The L steering matrices may then be generated as follows:
 
   V   ( l   1   l   2    . . . l   Q )= Ω   1   l     1   · Ω   2   l     2   · . . . · Ω   Q   l     Q     · V     0 , for l 1 , l 2 , . . . , l Q ε{0,1},  Eq (26)
 
where  V   0  is an N ap ×N S  independent isotropically distributed unitary matrix; and
           Ω   j   l     j   , for j=1 . . . Q, is an N ap ×N ap  independent isotropically distributed unitary matrix.
 
The matrix  V   0  may be defined, for example, as  V   0   T =[ I   N     S      0 ], where  I   N     S    is an N S ×N S  identity matrix. The second scheme is described by T. L. Marzetta et al. in “Structured Unitary Space-Time Autocoding Constellations,” IEEE Transaction on Information Theory, Vol. 48, No. 4, April 2002.
       

     In a third scheme, the L steering matrices are generated by successively rotating an initial unitary steering matrix  V (1) in an Nap-dimensional complex space, as follows:
 
   V   ( i+ 1)= Θ   i   · V   (1), for  i= 1  . . . L− 1,  Eq (27)
 
where  Θ   i  is an N ap ×N ap  diagonal unitary matrix that may be defined as:
 
                         Θ   _     i     =     [           ⅇ     j   ⁢           ⁢   2   ⁢           ⁢     π   ·     u   1     ·     i   /   L               0       ⋯       0           0         ⅇ     j   ⁢           ⁢   2   ⁢           ⁢     π   ·     u   2     ·     i   /   L               ⋯       0           ⋮       ⋮       ⋰       ⋮           0       0       ⋯         ⅇ     j   ⁢           ⁢   2   ⁢           ⁢     π   ·     u     N   ap       ·     i   /   L                 ]       ,           Eq   ⁢           ⁢     (   28   )                 
and u 1 , u 2 , . . . u N     ap    are N ap  different values, each within the range of 0 to L−1, which are chosen such that, e.g., the correlation between the resulting steering matrices generated with the matrix  Θ   i  is as low as possible. The N ap  diagonal elements of  Θ   i  are L-th roots of unity. The initial unitary steering matrix  V (1) may be formed with N S  different columns of an N ap ×N ap  Fourier matrix where the (n,m)-th entry, w n,m , is given as:
 
                 w     n   ,   m       =     ⅇ       -   j     ⁢           ⁢   2   ⁢           ⁢   π   ⁢         (     n   -   1     )     ⁢     (     m   -   1     )         N   ap             ,         for n={1 . . . N ap } and m{1 . . . N ap },  Eq (29)
 
where n is a row index and m is a column index. The third scheme is described by B. M. Hochwald et al. in “Systematic Design of Unitary Space-Time Constellations,” IEEE Transaction on Information Theory, Vol. 46, No. 6, September 2000.
 
     In a fourth scheme, the L steering matrices are generated with a base matrix  B  and different scalars. The base matrix may be a Walsh matrix, a Fourier matrix, or some other matrix. A 2×2 Walsh matrix may be expressed as 
                 W   _       2   ⨯   2       =       [         1       1           1         -   1           ]     .           
A larger size Walsh matrix  W   2N×2N  may be formed from a smaller size Walsh matrix  W   N×N , as follows:
 
                       W   _       2   ⁢     N   ⨯   2     ⁢   N       =       [             W   _       N   ⨯   N             W     N   ⨯   N                   W   _       N   ⨯   N             -       W   _       N   ⨯   N               ]     .   __             Eq   ⁢           ⁢     (   30   )                 
Walsh matrices have dimensions that are powers of two. An N ap ×N ap  Fourier matrix  F  may be formed with elements defined as shown in equation (29).
 
     An N ap ×N ap  Walsh matrix  W , Fourier matrix  F , or some other matrix may be used as the base matrix  B  to form other steering matrices. Each of rows  2  through Nap of the base matrix may be independently multiplied with one of M different possible scalars, where M&gt;1. M N     ap     −1  different steering matrices may be obtained from M N     ap     −1  different permutations of the M scalars for the N ap −1 rows. For example, each of rows  2  through Nap may be independently multiplied with a scalar of +1, −1,+j, or −j, where i=√{square root over (−1)}. For N ap =4 and M=4, 64 different steering matrices may be generated from the base matrix  B  with the four different scalars. Additional steering matrices may be generated with other scalars, e.g., e ±j3π/4 , e ±jπ/4 , e ±jπ/8 , and so on. In general, each row of the base matrix may be multiplied with any scalar having the form e jθ , where θ may be any phase value. N ap ×N ap  steering matrices may be generated as  V (i)=g N     ap   · B (i), where g N     ap   =1/√{square root over (N ap )} and  B (i) is the i-th matrix generated with the base matrix  B . The scaling by g N     ap    ensures that each column of  V (i) has unit power. 
     Other schemes may also be used to generate the set of L steering matrices, and this is within the scope of the invention. In general, the steering matrices may be generated in a pseudo-random manner (e.g., such as the first scheme) or a deterministic manner (e.g., such as the second, third, and fourth schemes). 
     B. Steering Vector Generation 
     The steering vectors used for spatial spreading in a MISO system should have unit energy, which is ∥ v (i)∥ 2 = v   H (i)· v (i)=1 for i=1 . . . L, so that the transmit power used for the data symbols is not varied by the spatial spreading. The elements of each steering vector  v (i) may be defined to have equal magnitude so that the full transmit power of each access point antenna can be used for broadcast. This condition may be expressed as: |v 1 (i)|=|v 2 (i)|= . . . =|v N     ap   (i)|, where  v (i)[v 1 (i) v 2 (i) . . . v N     ap   (i)]. Some of the steering vectors may also be uncorrelated so that the correlation between any two uncorrelated steering vectors is zero or a low value. This condition may be expressed as:
 
 c ( ij )=   v     H ( i )·   v   ( j )≈0, for i=1  . . . L, j= 1  . . . L , and  i≠j,   Eq (31)
 
where c(ij) is the correlation between steering vectors  v (i) and  v (j).
 
     The set of L steering vectors { v } may be generated using various schemes. In a first scheme, the L steering vectors are generated based on N ap ×N ap  matrices  G′  of random variables. An N ap ×N ap  correlation matrix of each matrix  G′  is computed as  R′ = G′   H · G′  and decomposed as shown in equation (25) to obtain an N ap ×N ap  unitary matrix  E′ . Each column of  E′  may be used as a steering vector  v (i). 
     In a second scheme, the L steering vectors are generated by successively rotating an initial unitary steering vector  v (1) as follows:
 
   v   ( i+ 1)= e   j2π/L   · v   ( i ), for  i= 2  . . . L,   Eq (32)
 
where L≧N ap .
 
     In a third scheme, the L steering vectors are generated such that the elements of these vectors have the same magnitude but different phases. For a given steering vector  v (i)=[v 1 (i) v 2  (i) . . . v N     ap   (i)], a normalized steering vector  {tilde over (v)} (i) may be formed as:
 
   {tilde over (v)}   ( i )=[ Ae   jθ     1     (i)    Ae   jθ     2     (i)    . . . Ae   jθ(i) ],  Eq (33)
 
where A is a constant (e.g., A=1/√{square root over (N ap )}); and
         θ j (i) is the phase of the j-th element of  v (i), which is:       

                       θ   j     ⁡     (   i   )       =       ∠   ⁢           ⁢       v   j     ⁡     (   i   )         =         tan     -   1       ⁡     (       Im   ⁢     {       v   j     ⁡     (   i   )       }         Re   ⁢     {       v   j     ⁡     (   i   )       }         )       .               Eq   ⁢           ⁢     (   34   )                 
The normalized steering vector  {tilde over (v)} (i) allows the full transmit power available for each antenna to be used for broadcast transmission.
 
     The columns of the steering matrices generated as described above may also be used as steering vectors for spatial spreading. Other schemes may also be used to generate the set of steering vectors, and this is within the scope of the invention. 
     The broadcast transmission techniques described herein may be implemented by various means. For example, these techniques may be implemented in hardware, software, or a combination thereof. For a hardware implementation, the processing units used to perform or support broadcast transmission with spatial spreading at the access point and the user terminal may be implemented within one or more application specific integrated circuits (ASICs), digital signal processors (DSPs), digital signal processing devices (DSPDs), programmable logic devices (PLDs), field programmable gate arrays (FPGAs), processors, controllers, micro-controllers, microprocessors, other electronic units designed to perform the functions described herein, or a combination thereof. 
     For a software implementation, the broadcast transmission techniques may be implemented with modules (e.g., procedures, functions, and so on) that perform the functions described herein. The software codes may be stored in memory units (e.g., memory units  442  and  482  in  FIG. 4  and memory units  842  and  882  in  FIG. 8 ) and executed by a processor (e.g., controllers  440  and  480  in  FIG. 4  and controllers  840  and  880  in  FIG. 8 ). The memory unit may be implemented within the processor or external to the processor, in which case it can be communicatively coupled to the processor via various means as is known in the art. 
     Headings are included herein for reference and to aid in locating certain sections. These headings are not intended to limit the scope of the concepts described therein under, and these concepts may have applicability in other sections throughout the entire specification. 
     The previous description of the disclosed embodiments is provided to enable any person skilled in the art to make or use the present invention. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the generic principles defined herein may be applied to other embodiments without departing from the spirit or scope of the invention. Thus, the present invention is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.