Patent Publication Number: US-11646761-B2

Title: Wireless device

Description:
CROSS-REFERENCE TO RELATED APPLICATION 
     This application is based upon and claims the benefit of priority of the prior Japanese Patent Application No. 2020-92672, filed on May 27, 2020, the entire contents of which are incorporated herein by reference. 
     FIELD 
     The disclosed technique discussed herein is related to a wireless device. 
     BACKGROUND 
     In recent years, regarding a wireless device using a high frequency band (for example, microwave band and millimeter-wave band), as one of techniques for multiplexing signals to be transmitted/received or enhancing accuracy of sensing (radar), beamforming is put into practical use. As the technique related to the wireless device to which beamforming is applied, the following technique has been known. 
     For example, a wireless device has been known that includes a first antenna element group, a full digital array that does not include an analog variable phase shifter, a second antenna element group including a plurality of antenna elements, and a hybrid beamformer that includes an analog variable phase shifter. 
     Furthermore, a wireless relay device has been known that includes a reception antenna, a transmission array antenna including a plurality of antenna elements, a Low Noise Amplifier (LNA), a noise removal Band pass filter (BPF), a mixer, a local oscillator, a narrow band BPF, an amplifier, a controller, an RF phase shifter, an image removal BPF, and a Power Amplifier (PA). 
     Furthermore, an image rejection mixer has been known that includes a distributor that divides an RF signal into two in the same phase, a distributor that divides a local signal into two with a phase difference of 90 degrees, and a first and a second mixers that mix distributed outputs of the respective distributors. This image rejection mixer includes two pairs of resistor and capacitance circuits connected to the outputs of the first and the second mixers in series, a load resistor connected to each of a connection point of a resistor and a connection point of a capacitance, and an IF output terminal that reduces image signals on one side of the load resistor. 
     International Publication Pamphlet No. WO 2017/135389, Japanese Laid-open Patent Publication No. 2003-332953, and Japanese Laid-open Patent Publication No. 5-191153 are disclosed as related art. 
     SUMMARY 
     According to an aspect of the embodiments, a wireless device includes: a plurality of antenna elements configured to form a plurality of transmission beams, each of the plurality of transmission beams being configured to transmit a corresponding transmission signal among a plurality of transmission signals; and a plurality of phase controller, each of the plurality of phase controller being couple to a corresponding antenna element among the plurality of antenna elements, each of the plurality of phase controller including: a plurality of phase control circuits corresponding to the plurality of transmission beams and configured to receive an input of the plurality of transmission signals to be transmitted from the corresponding antenna element, each of the plurality of phase control circuits being a circuit allocated to among the plurality of transmission beams a corresponding transmission beam to be used to transmit a corresponding transmission signal among the plurality of transmission signals, each of the plurality of phase control circuits being configured to output a phase controlled transmission signal by controlling, based on a transmission direction of the corresponding transmission beam, a phase of the corresponding transmission signal, and a plurality of mixers, each of the plurality of mixers being allocated to a corresponding phase control circuit among the plurality of phase control circuits, each of the plurality of mixers being configured to output an up-converted signal by up-converting, in response to inputting of the phase controlled transmission signal from the corresponding phase control circuit, a frequency of the phase controlled transmission signal, the up-converted signals output from the plurality of mixers are merged and radiated from the corresponding antenna element. 
     The object and advantages of the invention will be realized and attained by means of the elements and combinations particularly pointed out in the claims. 
     It is to be understood that both the foregoing general description and the following detailed description are exemplary and explanatory and are not restrictive of the invention. 
    
    
     
       BRIEF DESCRIPTION OF DRAWINGS 
         FIG.  1    is a diagram illustrating an example of a configuration of a wireless device according to a first reference example; 
         FIG.  2    is a diagram illustrating an example of a configuration of a wireless system according to an embodiment of the disclosed technique; 
         FIG.  3    is a diagram illustrating an example of a configuration of a wireless device according to the embodiment of the disclosed technique; 
         FIG.  4    is a diagram illustrating an example of a configuration of a phase control circuit according to the embodiment of the disclosed technique; 
         FIG.  5    is a diagram illustrating an example of a configuration of a phase control circuit according to a second reference example; 
         FIG.  6    is a diagram illustrating an example of the configuration of the phase control circuit according to the second reference example; 
         FIG.  7    is a diagram illustrating an example of the configuration of the phase control circuit according to the embodiment of the disclosed technique; 
         FIG.  8    is a diagram illustrating an example of the configuration of the phase control circuit according to the embodiment of the disclosed technique; 
         FIG.  9    is a diagram illustrating an example of a configuration of a phase control circuit according to a second embodiment of the disclosed technique; 
         FIG.  10    is a diagram illustrating an example of a configuration of a phase control circuit according to a third embodiment of the disclosed technique; 
         FIG.  11    is a diagram illustrating an example of a configuration of a phase control circuit according to a fourth embodiment of the disclosed technique; 
         FIG.  12    is a diagram illustrating an example of a configuration of a phase control circuit according to a fifth embodiment of the disclosed technique; 
         FIG.  13    is a diagram illustrating an example of a configuration of a phase control circuit according to a sixth embodiment of the disclosed technique; 
         FIG.  14    is a diagram illustrating an example of a configuration of a phase control circuit according to a seventh embodiment of the disclosed technique; 
         FIG.  15 A  is a diagram illustrating an example of a configuration of a phase control circuit according to an eighth embodiment of the disclosed technique; 
         FIG.  15 B  is a diagram illustrating an example of the configuration of the phase control circuit according to the eighth embodiment of the disclosed technique; 
         FIG.  16    is a diagram illustrating an example of a configuration of a phase control circuit according to a ninth embodiment of the disclosed technique; 
         FIG.  17    is a diagram illustrating only a configuration portion related to one of signals in a baseband region or an intermediate frequency band of the phase control circuit according to the ninth embodiment of the disclosed technique; 
         FIG.  18 A  is a table illustrating an example of an operation of the phase control circuit according to the ninth embodiment of the disclosed technique; 
         FIG.  18 B  is a table illustrating an example of an operation of the phase control circuit according to the ninth embodiment of the disclosed technique; 
         FIG.  18 C  is a table illustrating an example of an operation of the phase control circuit according to the ninth embodiment of the disclosed technique; 
         FIG.  18 D  is a table illustrating an example of an operation of the phase control circuit according to the ninth embodiment of the disclosed technique; 
         FIG.  19    is a diagram illustrating an example of a configuration of a phase control circuit according to a tenth embodiment of the disclosed technique; 
         FIG.  20    is a diagram illustrating only a configuration portion related to one of signals in a baseband region or an intermediate frequency band of the phase control circuit according to the tenth embodiment of the disclosed technique; 
         FIG.  21 A  is a table illustrating an example of an operation of the phase control circuit according to the tenth embodiment of the disclosed technique; 
         FIG.  21 B  is a table illustrating an example of an operation of the phase control circuit according to the tenth embodiment of the disclosed technique; 
         FIG.  21 C  is a table illustrating an example of an operation of the phase control circuit according to the tenth embodiment of the disclosed technique; 
         FIG.  21 D  is a table illustrating an example of an operation of the phase control circuit according to the tenth embodiment of the disclosed technique; 
         FIG.  22 A to  22 C  are diagrams illustrating an example of a configuration of a phase control circuit according to an eleventh embodiment of the disclosed technique; 
         FIG.  23    is a diagram illustrating only a configuration portion related to one of signals in a baseband region or an intermediate frequency band of the phase control circuit according to the eleventh embodiment of the disclosed technique; 
         FIG.  24 A  is a table illustrating an example of an operation of the phase control circuit according to the eleventh embodiment of the disclosed technique; 
         FIG.  24 B  is a table illustrating an example of an operation of the phase control circuit according to the eleventh embodiment of the disclosed technique; 
         FIG.  24 C  is a table illustrating an example of an operation of the phase control circuit according to the eleventh embodiment of the disclosed technique; 
         FIG.  24 D  is a table illustrating an example of an operation of the phase control circuit according to the eleventh embodiment of the disclosed technique; 
         FIG.  24 E  is a table illustrating an example of an operation of the phase control circuit according to the eleventh embodiment of the disclosed technique; 
         FIG.  24 F  is a table illustrating an example of an operation of the phase control circuit according to the eleventh embodiment of the disclosed technique; 
         FIG.  24 G  is a table illustrating an example of an operation of the phase control circuit according to the eleventh embodiment of the disclosed technique; and 
         FIG.  25    is a diagram illustrating a modification of the phase control circuit according to the eleventh embodiment of the disclosed technique. 
     
    
    
     DESCRIPTION OF EMBODIMENTS 
     A wireless device that performs beamforming forms a beam for each terminal using a plurality of antenna elements. Beamforming is realized by controlling at least one of a phase and an amplitude of a signal transmitted or received via each antenna element according to a position of the terminal so as to control a direction and a shape of a transmission beam or a reception beam. 
     Furthermore, a wireless device has been developed that superimposes a plurality of different signals and to which beam multiplexing for forming beams in different directions is applied. As one of methods for realizing beam multiplexing, full-digital system beamforming has been proposed. 
     In the full-digital system beamforming, at least one of the phase or the amplitude of the signal transmitted or received via each antenna element is controlled by digital processing. Therefore, the wireless device that performs full-digital beamforming includes a digital/analog converter (DAC) on each antenna element in order to form the transmission beams. In other words, for example, the wireless device that performs the full-digital system beamforming includes the DACs as many as the antenna elements. Furthermore, the wireless device that performs the full-digital system beamforming includes analog/digital converters (ADCs) as many as the antenna elements in order to form the reception beams. Here, power consumption of the DAC and the ADC depends on a rate of a data signal. Therefore, in a case where the wireless device that performs the full-digital system beamforming is applied to, for example, a broadband communication system that uses a millimeter-wave band or the like, the rate of the data signal increases, and the power consumption increases. 
     As another system for realizing beamforming, an analog full connection system has been proposed.  FIG.  1    is a diagram illustrating an example of a configuration of a wireless device (first reference example) that performs analog full connection system beamforming. 
     A wireless device  10 X illustrated in  FIG.  1    includes four DACs  12  to house four terminals (not illustrated). Each DAC  12  converts a transmission signal to be transmitted to the terminal into an analog signal. However, it is preferable that the wireless device  10 X include the larger number of antenna elements than the number of terminals (in other words, for example, the number of transmission signals). In the example illustrated in  FIG.  1   , the wireless device  10 X includes eight antenna elements AN. In this case, transmission signals ST 1  to ST 4  in a baseband region or an intermediate frequency band to be transmitted to the respective terminals are distributed to the eight phase control circuits  20 X provided in correspondence with the respective antenna elements AN after being up-converted to a Radio Frequency (RF) band using a local signal LO. Each of the phase control circuits  20 X control phases of the transmission signals ST 1  to ST 4 . Then, an output signal of the phase control circuit  20 X is output via the corresponding antenna element AN, respectively. Each of the phase control circuits  20 X controls each of the phases of the transmission signals ST 1  to ST 4  according to the position of the terminal so as to form a beam corresponding to each terminal. 
     According to the analog full connection system, it is sufficient that the DACs  12  as many as the terminals (the number of signals) be included. Therefore, the number of DACs can be reduced in comparison with that in the full digital system, and this can reduce the power consumption. However, according to the analog full connection system, a large number of signal lines intersect with each other between the plurality of DACs  12  and the plurality of phase control circuits  20 X. In the example illustrated in  FIG.  1   , 32 signal lines are provided between the four DACs  12  and the eight phase control circuits  20 X, and signals in the RF band having a relatively high frequency are transmitted through these signal lines. Therefore, a loss of the signals is large, and it is difficult to practically use this wireless device. 
     In order to solve the above problems, for example, it is considered to add a loss compensation circuit. However, in a case where miniaturization of the wireless device is requested, it is not preferable to add the loss compensation circuit because a circuit size (occupied area of circuit) increases. Furthermore, there is a possibility that the power consumption is increased by adding the loss compensation circuit. 
     An object of one aspect of the disclosed technique is to reduce a loss of signals while suppressing an increase in a circuit size (occupied area of circuit) in a wireless device that performs beamforming. 
     An example of an embodiment of the disclosure will be described below with reference to the drawings. Note that, in each drawing, the same or equivalent components and portions are denoted with the same reference numerals, and redundant explanation will be omitted. 
     First Embodiment 
       FIG.  2    is a diagram illustrating an example of a configuration of a wireless system  200  according to an embodiment of the disclosed technique. The wireless system  200  includes a wireless device  10  and a plurality of terminals  101 ,  102 ,  103 , and  104 . The wireless device  10  is not particularly limited. However, for example, the wireless device  10  is mounted on a base station of a wireless system. In this case, the terminals  101  to  104  are user terminals such as smartphones. Note that, in the present embodiment, the number of terminals contained in the wireless system  200  is four. However, the number of terminals contained in the wireless system  200  can be appropriately increased or decreased. The wireless device  10  can form a transmission beam for transmitting signals to the terminals  101  to  104  and a reception beam for receiving signals from the terminals  101  to  104 . In other words, for example, the wireless device  10  has a function for forming the transmission beam to transmit the signals and a function for forming the reception beam to receive the signals. In the following, the signal transmission function will be mainly described. 
     Transmission signals ST 1  to ST 4  to be transmitted to the terminals  101  to  104 , respectively are given to the wireless device  10 . The wireless device  10  forms transmission beams B 1  to B 4  used to transmit the transmission signals ST 1  to ST 4  to the terminals  101  to  104 , respectively. The transmission beam B 1  is formed to transmit the transmission signal ST 1  from the wireless device  10  to the terminal  101 . Therefore, the transmission beam B 1  is formed in a direction from the wireless device  10  toward the terminal  101 . Similarly, the transmission beams B 2  to B 4  are formed to transmit the transmission signals ST 2  to ST 4  from the wireless device  10  to the terminals  102  to  104 , respectively. In this way, the wireless device  10  can simultaneously form the plural transmission beams B 1  to B 4  corresponding to the terminals  101  to  104 . The wireless device  10  individually controls radiation directions and shapes of the transmission beams B 1  to B 4  according to positions of the terminals  101  to  104 . In other words, for example, the wireless device  10  realizes beam multiplexing. 
       FIG.  3    is a diagram illustrating an example of a configuration of the wireless device  10  according to the embodiment of the disclosed technique. The wireless device  10  includes a plurality of phase control circuits  20 , a plurality of antenna elements AN, and a controller  30 . Note that, in  FIG.  3   , a reception circuit that forms reception beams is not illustrated. It is preferable that the number of antenna elements AN included in the wireless device  10  be larger than the number of terminals contained in the wireless system  200 . In the present embodiment, the four terminals  101  to  104  are contained in the wireless system  200 , and the eight antenna elements AN are included in the wireless device  10 . The antenna elements AN are arranged in an array. In other words, for example, the wireless device  10  includes an array antenna system. The plurality of antenna elements AN may be aligned in line or may be arranged in a matrix so as to form rows and columns. Furthermore, the antenna elements AN may be three-dimensionally arranged. 
     The phase control circuit  20  is provided in correspondence with each of the plurality of antenna elements AN. In other words, for example, the number of phase control circuits  20  included in the wireless device  10  is the same as the number of antenna elements AN and is eight in the present embodiment. The transmission signals ST 1  to ST 4  are analog signals in a baseband region or an intermediate frequency band. Frequencies of the transmission signals ST 1  to ST 4  are not particularly limited. However, the frequencies of the transmission signals ST 1  to ST 4  are, for example, about 3 GHz. Note that, in a case where a transmission signal given to the wireless device  10  is a digital signal, the wireless device  10  includes a digital/analog converter that converts the digital signal into an analog signal. The transmission signals ST 1  to ST 4  converted into an analog format by the digital/analog converter are distributed to each of the eight phase control circuits  20 . Each phase control circuit  20  controls phases of the transmission signals ST 1  to ST 4  using a weight W supplied from the controller  30  so as to form the transmission beams B 1  to B 4  used to transmit the transmission signals ST 1  to ST 4  to the terminals  101  to  104 . In other words, for example, the wireless device  10  performs analog full connection system beamforming for distributing the transmission signals ST 1  to ST 4  to be transmitted to the terminals  101  to  104  to all the phase control circuits  20  included in the wireless device  10  and forming the transmission beams B 1  to B 4 . 
     The controller  30  generates the weight W to control the phase by each of the phase control circuits  20  based on the positions of the terminals  101  to  104 . Each of the phase control circuits  20  performs phase control, indicated by the following formula (1) using the weight W generated by the controller  30 , on the transmission signals ST 1  to ST 4  so as to output signals S out1  to S out8 . 
     
       
         
           
             
               
                 
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     For example, the output signal S out1  output from one of the eight phase control circuits  20  is expressed by the following formula (2).
 
[Formula 2]
 
 S   out1   =W   1,1   ·ST 1+ W   1,2   ·ST 2+ W   1,3   ·ST 3+ W   1,4   ·ST 4  (2)
 
     The controller  30  generates weights W 1,1 , W 2,1 , W 3,1 , W 4,1 , W 5,1 , W 6,1 , W 7,1 , and W 8,1  on the basis of the position of the terminal  101 . Furthermore, the controller  30  generates weights W 1,2 , W 2,2 , W 3,2 , W 4,2 , W 5,2 , W 6,2 , W 7,2 , and W 8,2  based on the position of the terminal  102 . Furthermore, the controller  30  generates weights W 1,3 , W 2,3 , W 3,3 , W 4,3 , W 5,3 , W 6,3 , W 7,3 , and W 8,3  based on the position of the terminal  103 . Furthermore, the controller  30  generates weights W 1,4 , W 2,4 , W 3,4 , W 4,4 , W 5,4 , W 6,4 , W 7,4 , and W 8,4  based on the position of the terminal  104 . The weight W is updated according to a change in the positions of the terminals  101  to  104 , a change in communication environment between the wireless device  10  and the terminals  101  to  104 , or the like. 
     Each of the respective phase control circuits  20  up-convert the transmission signals ST 1  to ST 4  in the baseband region or the intermediate frequency band to an RF band (or millimeter waveband) using a local signal LO and output the up-converted signals as the output signals S out  to S out8 . The output signals S out1  to S out8  are radiated from the antenna elements AN to which correspond, respectively. By radiating the output signals S out1  to S out8 , of which the phases have been controlled, from the eight antenna elements AN, respectively, the transmission beams B 1  to B 4  toward the terminals  101  to  104 , respectively are formed. In other words, the wireless device  10  configures the array antenna system to form the transmission beams B 1  to B 4 . 
       FIG.  4    is a diagram illustrating an example of a configuration of the phase control circuit  20 . The configurations of the plurality of phase control circuits  20  are the same. Note that, in  FIG.  4   , the phase control circuit  20  that outputs the output signal S out1  among from the eight phase control circuits  20  is illustrated. The phase control circuit  20  includes a plurality of phase control units  40 , a plurality of mixer units  50 , and a combining unit  60 . The plurality of phase control units  40  and the plurality of mixer units  50  are provided in correspondence with the transmission signals ST 1  to ST 4  to be transmitted to the terminals  101  to  104 , respectively. 
     In the phase control unit  40 , for example, each passive circuit portion is configured to include at least one of a lumped parameter circuit and a circuit similar to the lumped parameter circuit such as a spiral inductor or a meander inductor, and the phase control unit  40  controls the phase of the transmission signal according to a transmission direction of the transmission signal (radiation direction of corresponding transmission beam) based on the weight W supplied from the controller  30 . Each phase control unit  40  includes a phase rotation unit  400 , a first phase switching unit  410   a , a second phase switching unit  410   b , a first variable amplifier  420   a , and a second variable amplifier  420   b . In each phase control unit  40 , a corresponding transmission signal is branched into two. One of the divided signals is supplied to the first phase switching unit  410   a , and the other is supplied to the phase rotation unit  400 . 
     The transmission signal of the transmission signals ST 1  to ST 4  is supplied to the first phase switching unit  410   a  without rotating its phase. In other words, for example, an in-phase signal ST 1 -I having the same phase as the transmission signal ST 1  is supplied to the first phase switching unit  410   a  corresponding to the transmission signal ST 1 . Similarly, in-phase signals ST 2 -I to ST 4 -I are supplied to the first phase switching units  410   a  corresponding to the transmission signals ST 2  to ST 4 , respectively. The first phase switching unit  410   a  selectively switches a phase rotation amount of the in-phase signal according to the transmission direction of the transmission signal. The first phase switching unit  410   a  rotates the phase of the corresponding in-phase signal by the selected rotation amount. For example, the first phase switching unit  410   a  corresponding to the transmission signal ST 1  selectively switches the phase rotation amount of the in-phase signal ST 1 -I according to the transmission direction of the transmission signal ST 1  (radiation direction of transmission beam B 1 ) and rotates the phase of the in-phase signal ST 1 -I. Similarly, the first phase switching units  410   a  corresponding to the transmission signals ST 2  to ST 4  selectively switch the phase rotation amounts of the in-phase signals ST 2 -I to ST 4 -I according to the transmission directions of the transmission signals ST 2  to ST 4  (radiation directions of transmission beams B 2  to B 4 ) and rotate the phases of the in-phase signals ST 2 -I to ST 4 -I. 
     The phase rotation unit  400  rotates the phase of the transmission signal among form the transmission signals ST 1  to ST 4  by 90°. In the following, a transmission signal of which the phase is rotated by 90° by the phase rotation unit  400  is referred to as a quadrature signal. In other words, for example, the phase rotation unit  400  corresponding to the transmission signal ST 1  outputs a quadrature signal ST 1 -Q. Similarly, the phase rotation units  400  corresponding to the transmission signals ST 2  to ST 4  output quadrature signals ST 2 -Q to ST 4 -Q, respectively. The quadrature signals ST 1 -Q to ST 4 -Q are supplied to the second phase switching units  410   b.    
     The second phase switching unit  410   b  selectively switches a phase rotation amount of the quadrature signal according to the transmission direction of the transmission signal. The second phase switching unit  410   b  rotates a phase of the quadrature signal by the selected rotation amount. For example, the second phase switching unit  410   b  corresponding to the transmission signal ST 1  selectively switches a phase rotation amount of the quadrature signal ST 1 -Q according to the transmission direction of the transmission signal ST 1  (radiation direction of transmission beam B 1 ) and rotates a phase of the quadrature signal ST 1 -Q. Similarly, the second phase switching units  410   b  corresponding to the transmission signals ST 2  to ST 4  each selectively switch phase rotation amounts of the quadrature signals ST 2 -Q to ST 4 -Q according to the transmission directions of the transmission signals ST 2  to ST 4  (radiation directions of transmission beams B 2  to B 4 ) and rotate phases of the quadrature signals ST 2 -Q to ST 4 -Q. The phase rotation amounts of the first phase switching unit  410   a  and the second phase switching unit  410   b  are set to either one of 0° or 180° based on the weight W supplied from the controller  30 . 
     The first variable amplifier  420   a  changes an amplitude of the output signal of the first phase switching unit  410   a  according to the transmission direction of the transmission signal. For example, the first variable amplifier  420   a  corresponding to the transmission signal ST 1  changes an amplitude of a signal obtained by rotating the phase of the in-phase signal ST 1 -I by 0° or 180° according to the transmission direction of the transmission signal ST 1 . Similarly, the first variable amplifiers  420   a  corresponding to the transmission signals ST 2  to ST 4  each change amplitudes of signals obtained by rotating the phases of the in-phase signals ST 2 -I to ST 4 -I by 0° or 180° according to the transmission directions of the transmission signals ST 2  to ST 4 . 
     The second variable amplifier  420   b  changes an amplitude of the output signal of the second phase switching unit  410   b  according to the transmission direction of the corresponding transmission signal. For example, the second variable amplifier  420   b  corresponding to the transmission signal ST 1  changes an amplitude of a signal obtained by rotating the phase of the quadrature signal ST 1 -Q by 0° or 180° according to the transmission direction of the transmission signal ST 1 . Similarly, the second variable amplifiers  420   b  corresponding to the transmission signals ST 2  to ST 4  each change amplitudes of signals obtained by rotating the phases of the quadrature signals ST 2 -Q to ST 4 -Q by 0° or 180° according to the transmission directions of the transmission signals ST 2  to ST 4 . Amplitude change rates (amplification rate) of the first variable amplifier  420   a  and the second variable amplifier  420   b  are set based on the weight W supplied from the controller  30 . 
     The plurality of mixer units  50  are provided in correspondence with the plurality of phase control units  40 , and each of mixer units  50  up-convert a frequency of the transmission signal of which the phase is controlled by the phase control unit  40 . Each mixer unit  50  includes a first mixer  500   a  and a second mixer  500   b . The first mixer  500   a  up-converts a frequency of the output signal of the first variable amplifier  420   a  using the local signal LO having a frequency higher than the frequencies of the transmission signals ST 1  to ST 4 . The second mixer  500   b  up-converts a frequency of the output signal of the second variable amplifier  420   b  using the local signal LO. Each of the plurality of mixer units  50  uses the common local signal LO. The transmission signals ST 1  to ST 4  in the baseband region or the intermediate frequency band are up-converted into the RF band (or millimeter waveband) by the mixer unit  50 . The frequency of the local signal LO is not particularly limited. However, for example, the frequency of the Local signal LO is about 25 GHz. The first mixer  500   a  and the second mixer  500   b  share (interconnect) a local terminal to which the local signal LO is input, and share (interconnect) an RF terminal from which an RF signal is output. 
     The combining unit  60  is a transmission path that connects the outputs of the plurality of mixer units  50  to each other. In other words, for example, the phase of each of the transmission signals ST 1  to ST 4  is controlled by the phase control unit  40  corresponding to each of transmission signals ST 1  to ST 4 , and the frequency is converted by the mixer unit  50 . Thereafter, the combining unit  60  synthesizes the transmission signals ST 11  to ST 4 . As a result, the phase control circuits  20  each generate the output signals S out1  to S out8 . The combining unit  60  is connected to the antenna element NA to which correspond, and the output signals S out1  to S out8  are radiated via the antenna elements AN. 
     By setting the phase rotation amounts of the first phase switching unit  410   a  and the second phase switching unit  410   b , it is possible to switch phase quadrants of the transmission signals ST 1  to ST 4 . The phase rotation amounts of the transmission signals ST 1  to ST 4  can be controlled within a range of 0° to 360° according to setting of the amplitude change rates (amplification rate) of the first variable amplifier  420   a  and the second variable amplifier  420   b . In other words, for example, each of the phase control units  40  control the phase rotation amounts of the transmission signals ST 1  to ST 4  within the range of 0° to 360° by synthesizing vectors of the in-phase signals and the quadrature signals of which the phases have been switched and the amplitudes have been controlled. 
     For example, in a case where the phase rotation amounts of the transmission signals ST 1  to ST 4  are controlled within the range of 0° to 90° (first quadrant) by the phase control unit  40 , 0° is selected as the phase rotation amount of the first phase switching unit  410   a . Furthermore, in this case, 0° is selected as the phase rotation amount of the second phase switching unit  410   b . It is possible to control the phase rotation amounts of the transmission signals ST 1  to ST 4  within the range of 0° to 90° according to a ratio of the amplification rates of the first variable amplifier  420   a  and the second variable amplifier  420   b.    
     Furthermore, for example, in a case where the phase rotation amounts of the transmission signals ST 1  to ST 4  are controlled within the range of 90° to 180° (second quadrant) by the phase control unit  40 , 180° is selected as the phase rotation amount of the first phase switching unit  410   a . Furthermore, in this case, 0° is selected as the phase rotation amount of the second phase switching unit  410   b . It is possible to control the phase rotation amounts of the transmission signals ST 1  to ST 4  within the range of 90° to 180° according to the ratio of the amplification rates of the first variable amplifier  420   a  and the second variable amplifier  420   b.    
     Furthermore, for example, in a case where the phase rotation amounts of the transmission signals ST 1  to ST 4  are controlled within the range of 180° to 270° (third quadrant) by the phase control unit  40 , 180° is selected as the phase rotation amount of the first phase switching unit  410   a . Furthermore, in this case, 180° is selected as the phase rotation amount of the second phase switching unit  410   b . It is possible to control the phase rotation amounts of the transmission signals ST 1  to ST 4  within the range of 180° to 270° according to the ratio of the amplification rates of the first variable amplifier  420   a  and the second variable amplifier  420   b.    
     Furthermore, for example, in a case where the phase rotation amounts of the transmission signals ST 1  to ST 4  are controlled within the range of 270° to 360° (fourth quadrant) by the phase control unit  40 , 0° is selected as the phase rotation amount of the first phase switching unit  410   a . Furthermore, in this case, 180° is selected as the phase rotation amount of the second phase switching unit  410   b . It is possible to control the phase rotation amounts of the transmission signals ST 1  to ST 4  within the range of 270° to 360° according to the ratio of the amplification rates of the first variable amplifier  420   a  and the second variable amplifier  420   b.    
     Furthermore, by changing the amplification rates of the first variable amplifier  420   a  and the second variable amplifier  420   b  while fixing the ratio of the amplification rates of the first variable amplifier  420   a  and the second variable amplifier  420   b , the amplitudes of the transmission signals ST 1  to ST 4  can be changed. In other words, for example, all elements of the weight W can weight, not only the phase but also the amplitude. For example, by weighting the amplitude, a beam shape such as a beam width of each of the transmission beams B 1  to B 4  can be independently changed. 
     Here, according to the wireless device  10 X in the first reference example illustrated in  FIG.  1   , the transmission signals ST 1  to ST 4  transmitted to the respective terminals are distributed to the plurality of phase control circuits  20 X after being up-converted to the RF band using the local signal LO. According to the wireless device  10 X in the first reference example, 32 signal lines are provided between four DACs  12  and the eight phase control circuits  20 X, and signals in the RF band of which a frequency is relatively high are transmitted through these signal lines. Therefore, a loss of the signals increases. 
     On the other hand, according to the wireless device  10  in the embodiment of the disclosed technique, the distribution of the transmission signals ST 1  to ST 4  to the phase control circuits  20  is performed in the baseband region or the intermediate frequency band having a relatively low frequency. Therefore, according to the wireless device  10  including the phase control circuits  20  in the embodiment of the disclosed technique, the loss of the signals can be reduced in comparison with the wireless device  10 X including the phase control circuits  20 X in the first reference example. 
       FIG.  5    is a diagram illustrating an example of a configuration of a phase control circuit  20 Y according to a second reference example. The phase control circuit  20 Y is provided in correspondence with each of the plurality of antenna elements AN. The phase control circuit  20 Y has functions similar to those of the phase control circuit  20  according to the embodiment of the above-disclosed technique. The phase control circuit  20 Y includes a plurality of amplitude control units  70 , a plurality of mixer units  50 Y, and a combining unit  60 . The plurality of amplitude control units  70  and the plurality of mixer units SOY are provided in correspondence with the respective transmission signals ST 1  to ST 4 . 
     Each amplitude control unit  70  changes an amplitude of the transmission signal according to the transmission direction of the transmission signal. The amplitude control unit  70  each includes a first variable amplifier  700   a  and a second variable amplifier  700   b . In each amplitude control unit  70 , the transmission signal is branched into two. One of the divided signals is supplied to the first variable amplifier  700   a , and the other is supplied to the second variable amplifier  700   b.    
     The first variable amplifier  700   a  and the second variable amplifier  700   b  each change the amplitudes of the transmission signals according to the transmission directions of the transmission signals. For example, the first variable amplifier  700   a  and the second variable amplifier  700   b  corresponding to the transmission signal ST 1  change the amplitude of the transmission signal ST 1  according to the transmission direction of the transmission signal ST 1 . Amplitude change rates (amplification rate) of the first variable amplifier  700   a  and the second variable amplifier  700   b  are set based on the weight W supplied from the controller  30 . 
     Each of the plurality of mixer units  50 Y includes a first phase switching unit  510   a , a second phase switching unit  510   b , a first mixer  500   a , and a second mixer  500   b . Each of the first phase switching unit  510   a  and the second phase switching unit  510   b  selectively switches the phase rotation amount of the local signal LO according to the transmission direction of the transmission signal. Each of the first phase switching unit  510   a  and the second phase switching unit  510   b  rotates the phase of the local signal LO by the selected rotation amount. The phase rotation amount of the first phase switching unit  510   a  is set to either one of 90° or 270° on the basis of the weight W supplied from the controller  30 . The phase rotation amount of the second phase switching unit  510   b  is set to either one of 0° or 180° on the basis of the weight W supplied from the controller  30 . 
     The first mixer  500   a  up-converts a frequency of the output signal of the first variable amplifier  700   a  using the local signal LO of which the phase is rotated by the first phase switching unit  510   a . The second mixer  500   b  up-converts a frequency of the output signal of the second variable amplifier  700   b  using the local signal LO of which the phase is rotated by the second phase switching unit  510   b . The mixer unit  50 Y up-converts the transmission signals ST 1  to ST 4  in the baseband region or the intermediate frequency band to the RF band (or millimeter waveband). 
     The amplitude of each of the transmission signals ST 1  to ST 4  is controlled by the amplitude control unit  70 , and the frequency is converted by the mixer unit  50 Y. Thereafter, the transmission signals ST 1  to ST 4  are synthesized by the combining unit  60 . As a result, the phase control circuits  20 Y each generate the output signals S out1  to S out8 . Note that, in  FIG.  5   , the phase control circuit  20 Y that outputs the output signal S out1  is illustrated. The combining unit  60  is connected to the antenna element NA, and the output signals S out1  to S out8  are radiated from the antenna elements AN to which correspond. 
     By setting the phase rotation amounts of the first phase switching unit  510   a  and the second phase switching unit  510   b , it is possible to switch phase quadrants of the transmission signals ST 1  to ST 4 . The phase rotation amounts of the transmission signals ST 1  to ST 4  can be controlled within a range of 0° to 360° according to setting of the amplitude change rates (amplification rate) of the first variable amplifier  700   a  and the second variable amplifier  700   b.    
     According to the phase control circuit  20 Y in the second reference example, it is possible to form transmission beams toward the terminals  101  to  104 , similarly to the phase control circuit  20  in the embodiment of the disclosed technique. Furthermore, the transmission signals ST 1  to ST 4  are distributed to the phase control circuits  20 Y in the baseband region or the intermediate frequency band where the frequency is relatively low. Therefore, a loss of the signals can be reduced in comparison with the wireless device  10 X according to the first reference example illustrated in  FIG.  1   . 
     However, according to the phase control circuit  20 Y in the second reference example, as illustrated in  FIG.  6   , the number of high frequency blocks HF through which the local signal LO having the relatively high frequency is transmitted increases. As illustrated in  FIG.  5   , for example, in a case where the four transmission signals ST 1  to ST 4  are used, the number of high frequency blocks HF is five. It is needed for each high frequency block HF to include a distributed constant circuit having a size according to a wavelength of a high frequency signal. Therefore, it is difficult to reduce the circuit size (occupied area of circuit) of the phase control circuit  20 Y in the second reference example. For example, in a case where the above circuit is configured on a semiconductor circuit chip, if the radio-frequency wavelength and the size of the semiconductor circuit chip become close to each other, the plurality of high frequency blocks HFs occupies most of a region in a semiconductor chip, and in addition, a chip area increases. 
     On the other hand, according to the phase control circuit  20  in the embodiment of the disclosed technique, as illustrated in  FIG.  7   , the number of high frequency blocks HF can be set to one. Furthermore, each mixer included in the mixer unit can be configured by a transistor  500 . Each of the transistors  500  has a common drain (or source) connected to the combining unit  60  and have a common gate to which the local signal LO is supplied. Therefore, the transistor  500  configuring the mixer can include a single drain electrode (or source electrode), a single gate electrode, and a single multi-finger type transistor including a plurality of separate source electrodes (or drain electrode). This makes it possible to make the plurality of mixer units  50  be exceedingly compact. In other words, for example, according to the phase control circuit  20  in the embodiment of the disclosed technique, the circuit size (occupied area of circuit) can be reduced in comparison with the phase control circuit  20 Y in the second reference example. 
     Furthermore, according to the phase control circuit  20  in the embodiment of the disclosed technique, the transmission signals ST 1  to ST 4  transmitted to the phase control units  40  are signals in the baseband region or the intermediate frequency band having a relatively low frequency. Therefore, a passive circuit of the phase control unit  40  can be configured to include a lumped parameter circuit or a circuit similar to the lumped parameter circuit. Here, the “circuit similar to the lumped parameter circuit” is a circuit that includes an element like a distributed constant circuit such as a spiral inductor or a meander inductor and that can be configured to have a small area. By configuring the passive element of the phase control unit  40  using the lumped parameter circuit or the circuit similar to the lumped parameter circuit, it is possible to reduce the circuit size (occupied area of circuit) of the phase control circuit  20  to be relatively small. 
     Note that, in  FIG.  4   , the configuration is illustrated in which the first variable amplifier  420   a  and the second variable amplifier  420   b  are arranged on the output sides of the first phase switching unit  410   a  and the second phase switching unit  410   b , respectively. However, the arrangement is not limited to this. In other words, for example, as illustrated in  FIG.  8   , the first variable amplifier  420   a  and the second variable amplifier  420   b  can be arranged on the input sides of the first phase switching unit  410   a  and the second phase switching unit  410   b , respectively. 
     Second Embodiment 
       FIG.  9    is a diagram illustrating an example of a configuration of a phase control circuit  20 A according to a second embodiment of the disclosed technique. The phase control circuit  20 A is provided in correspondence with each of a plurality of antenna elements AN. 
     The phase control circuit  20 A includes a plurality of phase rotation units  80 . The plurality of phase rotation units  80  is provided in correspondence with transmission signals ST 1  to ST 4 , respectively. The phase rotation unit  80  rotates a phase of the corresponding transmission signal by 90°. In other words, for example, the phase rotation unit  80  corresponding to the transmission signal ST 1  outputs a quadrature signal ST 1 -Q. Similarly, the phase rotation units  80  corresponding to the transmission signals ST 2  to ST 4  each output quadrature signals ST 2 -Q to ST 4 -Q. 
     In the phase control circuit  20 A, each of a plurality of phase control units provided in correspondence with the transmission signals ST 1  to ST 4  include a first to fourth phase switching units  410   a  to  410   d  and a first to fourth variable amplifiers  420   a  to  420   d.    
     Each of the first and the third phase switching units  410   a  and  410   c  selectively switches a phase rotation amount of an in-phase signal according to a transmission direction of the transmission signal. The first and the third phase switching units  410   a  and  410   c  rotate a phase of the in-phase signal by the selected rotation amount. For example, the first and the third phase switching units  410   a  and  410   c  corresponding to the transmission signal ST 1  selectively switch a phase rotation amount of an in-phase signal ST 1 -I according to the transmission direction of the transmission signal ST 1  and rotates a phase of the in-phase signal ST 1 -I. 
     Each of the second and the fourth phase switching units  410   b  and  410   d  selectively switches a phase rotation amount of a quadrature signal according to transmission directions of the transmission signals. The second and the fourth phase switching units  410   b  and  410   d  rotate a phase of the quadrature signal by the selected rotation amount. For example, the second and the fourth phase switching units  410   b  and  410   d  corresponding to the transmission signal ST 1  selectively switch a phase rotation amount of a quadrature signal ST 1 -Q according to the transmission direction of the transmission signal ST 1  and rotates a phase of the in-phase signal ST 1 -Q. The phase rotation amounts of the first to the fourth phase switching units  410   a  to  410   d  are set to ether one of 0° or 180° on the basis of a weight W supplied from a controller  30 . 
     The first variable amplifier  420   a  changes an amplitude of the output signal of the first phase switching unit  410   a  according to the transmission direction of the transmission signal. Similarly, the second to the fourth variable amplifiers  420   b  to  420   d  each change amplitudes of output signals of the second to the fourth phase switching units  410   b  to  410   d  according to the transmission directions of the transmission signals. Amplitude change rates (amplification rate) of the first to the fourth variable amplifiers  420   a  to  420   d  are set based on the weight W supplied from the controller  30 . 
     In the phase control circuit  20 A, a plurality of mixer units provided in correspondence the transmission signals ST 1  to ST 4  each include a first to a fourth mixers  500   a  to  500   d . The first mixer  500   a  up-converts a frequency of the output signal of the first variable amplifier  420   a  using a first local signal LO-I having a frequency higher than frequencies of the transmission signals ST 1  to ST 4 . The second mixer  500   b  up-converts a frequency of the output signal of the second variable amplifier  420   b  using the first local signal LO-I. In other words, for example, the first mixer  500   a  and the second mixer  500   b  up-convert the frequencies using the common first local signal LO-I. 
     The third mixer  500   c  up-converts a frequency of the output signal of the third variable amplifier  420   c  using a second local signal LO-Q obtained by rotating a phase of the first local signal LO-I by 90°. The fourth mixer  500   d  up-converts a frequency of the output signal of the fourth variable amplifier  420   d  using the second local signal LO-Q. In other words, for example, the third mixer  500   c  and the fourth mixer  500   d  up-convert the frequencies using the common second local signal LO-Q. 
     The phases of the transmission signals ST 1  to ST 4  are controlled by the phase control units (first to fourth phase switching units  410   a  to  410   d  and first to fourth variable amplifiers  420   a  to  420   d ) respectively, and the frequencies are converted by the mixer units (first to fourth mixers  500   a  to  500   d ). Thereafter, the transmission signals ST 1  to ST 4  are synthesized by a combining unit  60 . With this operation, in each of the phase control circuits  20 A, the output signals S out1  to S out8  is generated. The combining unit  60  is connected to the antenna element NA to which correspond, and the output signals S out1  to S out8  are radiated from the antenna elements AN. Note that  FIG.  9    illustrates the phase control circuit  20 A that outputs the output signal S out1 . 
     Here, when the transmission signals ST 1  to ST 4  in a baseband region or an intermediate frequency band are mixed with the local signal using the mixers so as to up-convert the frequencies of the transmission signals ST 1  to ST 4 , an image signal is mixed into the output signal of the mixer. The image signal is a disturbing signal generated in a frequency band that is symmetrically provided with a desired signal with respect to a frequency band of the local signal. It is possible to reduce the image signals by mixing in-phase signals ST 1 -I to ST 4 -I, quadrature signals ST 1 -Q to ST 4 -Q, and the two local signals LO-I and LO-Q orthogonal to each other with the mixer, and then, combining the signals. 
     The phase control circuit  20 A has a configuration in which the third and the fourth phase switching units  410   c  and  410   d , the third and the fourth variable amplifiers  420   c  and  420   d , and the third and the fourth mixers  500   c  and  500   d  are added to the phase control circuit  20  in the first embodiment. With this configuration, because the processing is performed for mixing the in-phase signals ST 1 -I to ST 4 -I, the quadrature signals ST 1 -Q to ST 4 -Q, and the two local signals LO-I and LO-Q orthogonal to each other and combining the signals, it is possible to reduce the image signals. 
     In the phase control circuit  20 A, the in-phase signals ST 1 -I to ST 4 -I and the quadrature signals ST 1 -Q to ST 4 -Q are used to switch four quadrants of the phases of the transmission signals ST 1  to ST 4  and also used to reduce the image signals. In this way, by using the in-phase signals and the quadrature signals to control the phases and to reduce the image signals, it is possible to suppress an increase in a circuit size (occupied area of circuit). 
     Furthermore, according to the phase control circuit  20 A, similarly to the phase control circuit  20  in the first embodiment, the transmission signals ST 1  to ST 4  are distributed to the phase control circuits  20 A in the baseband region or the intermediate frequency band where the frequency is relatively low. Therefore, according to a wireless device  10  including the phase control circuit  20 A, a loss of signals can be reduced in comparison with the wireless device  10 X in the first reference example. Furthermore, according to the phase control circuit  20 A, because the number of high frequency blocks HF can be reduced similarly to the phase control circuit  20  in the first embodiment, an increase in a circuit size (occupied area of circuit) can be suppressed. Furthermore, the first mixer  500   a  and the second mixer  500   b  share (interconnect) a local terminal to which the first local signal LO-I is input, and the third mixer  500   c  and the fourth mixer  500   d  share (interconnect) a local terminal to which the second local signal LO-Q is input. Moreover, the first to the fourth mixers  500   a  to  500   d  share (interconnect) an RF terminal from which an RF signal is output. As a result, the mixer unit can be configured by, for example, a multi-finger type transistor, and it is possible to configure the mixer unit to be exceedingly compact. 
     Note that, as in the example illustrated in  FIG.  8   , the first to the fourth variable amplifiers  420   a  to  420   d  can be arranged on the input sides of the first to the fourth phase switching units  410   a  to  410   d , respectively. 
     Third Embodiment 
       FIG.  10    is a diagram illustrating an example of a configuration of a phase control circuit  20 B according to a third embodiment of the disclosed technique. The phase control circuit  206  is provided in correspondence with each of a plurality of antenna elements AN. The phase control circuit  20 B has a configuration in which a function for reducing image signals is added to the phase control circuit  20 Y in the second reference example illustrated in  FIG.  5   . 
     The phase control circuit  208  includes a plurality of phase rotation units  80 , a plurality of first amplitude control units  70 A, a plurality of second amplitude control units  70 B, a plurality of first mixer units  50 A, a plurality of second mixer units  50 B, and a combining unit  60 . 
     The plurality of phase rotation units  80  is provided in correspondence with transmission signals ST 1  to ST 4 , respectively. The phase rotation unit  80  rotates a phase of the transmission signal by 90°. In other words, for example, the phase rotation unit  80  corresponding to the transmission signal ST 1  outputs a quadrature signal ST 1 -Q. Similarly, the phase rotation units  80  corresponding to the transmission signals ST 2  to ST 4  each output quadrature signals ST 2 -Q to ST 4 -Q. 
     The plurality of first amplitude control units  70 A and the plurality of first mixer units  50 A are each provided in correspondence with the transmission signals ST 1  to ST 4 . Similarly, the plurality of second amplitude control units  708  and the plurality of second mixer units  50 B are each provided in correspondence with the transmission signals ST 1  to ST 4 . 
     Each first amplitude control unit  70 A changes an amplitude of the transmission signal. Each first amplitude control unit  70 A includes a first variable amplifier  700   a  and a second variable amplifier  700   b . In each first amplitude control unit  70 A, the transmission signal is branched into two. One of the divided signals is supplied to the first variable amplifier  700   a , and the other is supplied to the second variable amplifier  700   b.    
     The first variable amplifier  700   a  and the second variable amplifier  700   b  each change the amplitudes of the transmission signals according to the transmission directions of the transmission signals. For example, each of the first variable amplifier  700   a  and the second variable amplifier  700   b  corresponding to the transmission signal ST 1  changes an amplitude of an in-phase signal ST 1 -I having the same phase as the transmission signal ST 1  according to a transmission direction of the transmission signal ST 1 . Amplitude change rates (amplification rate) of the first variable amplifier  700   a  and the second variable amplifier  700   b  are set based on the weight W supplied from the controller  30 . 
     Each of the plurality of second amplitude control units  70 B changes an amplitude of a quadrature signal obtained by rotating a phase of the transmission signal by 90°. Each second amplitude control unit  70 B includes a third variable amplifier  700   c  and a fourth variable amplifier  700   d . In the second amplitude control unit  70 B, the quadrature signal is divided into two. One of the divided signal is supplied to the third variable amplifier  700   c , and the other is supplied to the fourth variable amplifier  700   d.    
     Each of the third variable amplifier  700   c  and the fourth variable amplifier  700   d  changes an amplitude of the quadrature signal according to the transmission direction of the transmission signal. For example, each of the third variable amplifier  700   c  and the fourth variable amplifier  700   d  corresponding to the transmission signal ST 1  changes an amplitude of a quadrature signal ST 1 -Q obtained by rotating a phase of the transmission signal ST 1  by 90° according to the transmission direction of the transmission signal ST 1 . Amplitude change rates (amplification rate) of the third variable amplifier  700   c  and the fourth variable amplifier  700   d  are set based on the weight W supplied from the controller  30 . 
     Each of the plurality of first mixer units  50 A includes a first phase switching unit  510   a , a first mixer  500   a , a second phase switching unit  510   b , and a second mixer  500   b . Each of the first phase switching unit  510   a  and the second phase switching unit  510   b  selectively switches a phase rotation amount of a first local signal LO-I according to the transmission direction of the transmission signal. The first phase switching unit  510   a  and the second phase switching unit  510   b  rotate a phase of the first local signal LO-I by the respectively selected rotation amount. The phase rotation amount of the first phase switching unit  510   a  is set to either one of 90° or 270° based on the weight W supplied from the controller  30 . The phase rotation amount of the second phase switching unit  510   b  is set to either one of 0° or 180° based on the weight W supplied from the controller  30 . 
     The first mixer  500   a  up-converts a frequency of the output signal of the first variable amplifier  700   a  using the first local signal LO-I of which the phase is rotated by the first phase switching unit  510   a . The second mixer  500   b  up-converts a frequency of the output signal of the second variable amplifier  700   b  using the first local signal LO-I of which the phase is rotated by the second phase switching unit  510   b . The transmission signals ST 1  to ST 4  in a baseband region or an intermediate frequency band are up-converted into an RF band (or millimeter waveband) by the plurality of first mixer units  50 A. 
     Each of the plurality of second mixer units SOB includes a third phase switching unit  510   c , a third mixer  500   c , a fourth phase switching unit  510   d , and a fourth mixer  500   d . Each of the third phase switching unit  510   c  and the fourth phase switching unit  510   d  selectively switches a phase rotation amount of a second local signal LO-Q obtained by rotating a phase by 90° with respect to the first local signal LO-I according to the transmission direction of the transmission signal. The third phase switching unit  510   c  and the fourth phase switching unit  510   d  rotate a phase of the second local signal LO-Q by the respectively selected rotation amount. The phase rotation amount of the third phase switching unit  510   c  is set to either one of 90° or 270° based on the weight W supplied from the controller  30 . The phase rotation amount of the fourth phase switching unit  510   d  is set to either one of 0° or 180° based on the weight W supplied from the controller  30 . 
     The third mixer  500   c  up-converts a frequency of the output signal of the third variable amplifier  700   c  using the second local signal LO-Q of which the phase is rotated by the third phase switching unit  510   c . The fourth mixer  500   d  up-converts a frequency of the output signal of the fourth variable amplifier  700   d  using the second local signal LO-Q of which the phase is rotated by the fourth phase switching unit  510   d . The transmission signals ST 1  to ST 4  in the baseband region or the intermediate frequency band are up-converted into the RF band (or millimeter waveband) by the plurality of second mixer units SOB. 
     An amplitude of each of the transmission signals ST 1  to ST 4  is controlled by the first amplitude control unit  70 A and second amplitude control unit  708 , and the frequency is converted by the first mixer unit  50 A and second mixer unit  50 B. Thereafter, the signals are combined by the combining unit  60 . With this operation, the phase control circuits  20 B each generate output signals S out1  to S out8 . Note that  FIG.  10    illustrates the phase control circuit  20 B that outputs the output signal S out1 . The combining unit  60  is connected to the antenna element NA to which correspond, and the output signals S out1  to S out8  are radiated from the antenna elements AN. 
     By setting the phase rotation amounts of the first to the fourth phase switching units  510   a  to  510   d , it is possible to switch phase quadrants of the transmission signals ST 1  to ST 4 . The phase rotation amounts of the respective transmission signals can be controlled within the range of 0° to 360° according to setting of the amplitude change rates (amplification rate) of the first to the fourth variable amplifiers  700   a  to  700   d.    
     According to the phase control circuit  20 B, similarly to the phase control circuit  20  in the first embodiment of the disclosed technique, it is possible to form a transmission beam toward each terminal. Furthermore, the transmission signals ST 1  to ST 4  are distributed to the phase control circuits  20 B in the baseband region or the intermediate frequency band where the frequency is relatively low. Therefore, a loss of the signals can be reduced in comparison with the wireless device  10 X in the first reference example (refer to  FIG.  1   ). 
     Furthermore, the phase control circuit  20 B has a configuration in which the phase rotation unit  80 , the third phase switching unit  510   c , the fourth phase switching unit  510   d , the third variable amplifier  700   c , the fourth variable amplifier  700   d , the third mixer  500   c , and the fourth mixer  500   d  are added to the phase control circuit  20 Y (refer to  FIG.  5   ) in the second reference example. With this configuration, because the processing is performed for mixing the in-phase signals ST 1 -I to ST 4 -I, the quadrature signals ST 1 -Q to ST 4 -Q and the two local signals LO-I and LO-Q orthogonal to each other and combining the signals, it is possible to reduce the image signals. 
     Fourth Embodiment 
       FIG.  11    is a diagram illustrating an example of a configuration of a phase control circuit  20 C in a fourth embodiment of the disclosed technique. The phase control circuit  20 C is provided in correspondence with each of a plurality of antenna elements AN. The phase control circuits  20 ,  20 A, and  20 B according to the above-described first to the third embodiments have the function for forming the transmission beams B 1  to B 4  toward the terminals  101  to  104  to transmit the transmission signals ST 1  to ST 4 . On the other hand, the phase control circuit  20 C according to the present embodiment has a function for forming a reception beam to receive signals (hereinafter, referred to as reception signals SR 1  to SR 4 ) transmitted from the terminals  101  to  104 . 
     The phase control circuit  20 C has a configuration corresponding to the phase control circuit  20  (refer to  FIG.  4   ) according to the first embodiment. In other words, for example, the phase control circuit  20 C includes a plurality of phase control units  40  and a plurality of mixer units  50 . The plurality of phase control units  40  and the plurality of mixer units  50  are provided in correspondence with each of the reception signals SR 1  to SR 4 . The phase control circuit  20 C receives an input signal S in  obtained by combining the reception signals SR 1  to SR 4  transmitted from the terminals  101  to  104 , respectively via the corresponding antenna element AN. The input signal S in  is distributed to the plurality of mixer units  50 . 
     The plurality of mixer units  50  is provided in correspondence with each of the reception signals SR 1  to SR 4 , and each mixer unit  50  down-converts a frequency of the input signal S in  obtained by combining the reception signals SR 1  to SR 4 . Each mixer unit  50  includes a first mixer  500   a  and a second mixer  500   b . Each of the first mixer  500   a  and the second mixer  500   b  down-converts the frequency of the input signal S in  in an RF band (or millimeter waveband) to a baseband region or an intermediate frequency band using a local signal LO. 
     The plurality of phase control units  40  is provided respectively in correspondence with the plurality of mixer units  50  and changes a phase of the signal of which the frequency is down-converted by the corresponding mixer unit  50  according to an arrival direction of the reception signal. 
     Each phase control unit  40  includes a phase rotation unit  400 , a first phase switching unit  410   a , a second phase switching unit  410   b , a first variable amplifier  420   a , and a second variable amplifier  420   b.    
     The first variable amplifier  420   a  changes an amplitude of an output signal of the first mixer  500   a  according to the arrival direction of the corresponding reception signal. Similarly, the second variable amplifier  420   b  changes an amplitude of an output signal of the second mixer  500   b  according to the arrival direction of the corresponding reception signal. Amplitude change rates (amplification rate) of the first variable amplifier  420   a  and the second variable amplifier  420   b  are set based on the weight W supplied from the controller  30 . 
     The first phase switching unit  410   a  selectively switches a rotation amount of the output signal of the first variable amplifier  420   a  according to the arrival direction of the reception signal. The first phase switching unit  410   a  rotates a phase of the output signal of the first variable amplifier  420   a  by the selected rotation amount and outputs the signal as an in-phase signal (SR 1 -I to SR 4 -I) of the reception signal. 
     The second phase switching unit  410   b  selectively switches a rotation amount of the output signal of the second variable amplifier  420   b  according to the arrival direction of the reception signal. The second phase switching unit  410   b  rotates a phase of the output signal of the second variable amplifier  420   b  by the selected rotation amount and outputs the signal as a quadrature signal (SR 1 -Q to SR 4 -Q) of the reception signal. The phase rotation amounts of the first phase switching unit  410   a  and the second phase switching unit  410   b  are set to either one of 0° or 180° on the basis of the weight W supplied from the controller  30 . 
     The phase rotation unit  400  generates an in-phase signal of the reception signal by rotating a phase of the quadrature signal (S 1 -Q to S 4 -Q) that is the output signal of the second phase switching unit  410   b  by 90°. The output signal of the first phase switching unit  410   a  and the output signal of the phase rotation unit  400  are combined, and accordingly, the reception signals SR 1  to SR 4  are separately extracted. 
     In this way, a flow of the signal in the phase control circuit  20 C is opposite to a flow of the signal in the phase control circuit  20  in the first embodiment, and a processing order is reversed. According to the phase control circuit  20 C in the present embodiment, similarly to the phase control circuit  20  in the first embodiment, it is possible to reduce a loss of signals while suppressing an increase in a circuit size (occupied area of circuit). Furthermore, the first mixer  500   a  and the second mixer  500   b  share (interconnect) a local terminal to which the local signal LO is input and share (interconnect) an RF terminal to which the input signal S in , which is an RF signal, is input. As a result, the mixer unit  50  can be configured by, for example, a multi-finger type transistor, and it is possible to configure the mixer unit  50  to be exceedingly compact. 
     Note that, as in the example illustrated in  FIG.  8   , the first variable amplifier  420   a  and the second variable amplifier  420   b  can be arranged on the output sides of the first phase switching unit  410   a  and the second phase switching unit  410   b , respectively. 
     Fifth Embodiment 
       FIG.  12    is a diagram illustrating an example of a configuration of a phase control circuit  20 D according to a fifth embodiment of the disclosed technique. The phase control circuit  20 D is provided in correspondence with each of a plurality of antenna elements AN. The phase control circuit  20 D has a function for forming a reception beam to receive signals transmitted from terminals  101  to  104 . 
     The phase control circuit  20 D has a configuration corresponding to the phase control circuit  20 A (refer to  FIG.  9   ) according to the second embodiment. A flow of the signal in the phase control circuit  20 D is opposite to the flow of the signal in the phase control circuit  20 A in the second embodiment, and a processing order is reversed. The phase control circuit  20 D receives an input signal S in  obtained by combining reception signals SR 1  to SR 4  transmitted from the terminals  101  to  104 , respectively and separately extracts the reception signals SR 1  to SR 4  included in the input signal S in . 
     According to the phase control circuit  20 D in the present embodiment, similarly to the phase control circuit  20 A in the second embodiment, it is possible to reduce a loss of signals while suppressing an increase in a circuit size (occupied area of circuit), and in addition, image signals can be reduced. Furthermore, the first mixer  500   a  and the second mixer  500   b  share (interconnect) a local terminal to which the first local signal LO-I is input, and the third mixer  500   c  and the fourth mixer  500   d  share (interconnect) a local terminal to which the second local signal LO-Q is input. Moreover, the first to the fourth mixers  500   a  to  500   d  share (interconnect) an RF terminal to which the input signal S in , which is an RF signal, is input. As a result, the mixer unit can be configured by, for example, a multi-finger type transistor, and it is possible to configure the mixer unit to be exceedingly compact. 
     Note that, as in the example illustrated in  FIG.  8   , a first to a fourth variable amplifiers  420   a  to  420   d  can be arranged on output sides of a first to a fourth phase switching units  410   a  to  410   d , respectively. 
     Sixth Embodiment 
       FIG.  13    is a diagram illustrating an example of a configuration of a phase control circuit  20 E according to a sixth embodiment of the disclosed technique. The phase control circuit  20 E is provided in correspondence with each of a plurality of antenna elements AN. The phase control circuit  20 E has a function for forming a reception beam to receive signals transmitted from terminals  101  to  104 . 
     The phase control circuit  20 E has a configuration corresponding to the phase control circuit  20 B (refer to  FIG.  10   ) in the third embodiment. A flow of the signal in the phase control circuit  20 E is opposite to the flow of the signal in the phase control circuit  20 B in the third embodiment, and a processing order is reversed. The phase control circuit  20 E receives an input signal S in  obtained by combining reception signals SR 1  to SR 4  transmitted from the terminals  101  to  104 , respectively and separately extracts the reception signals SR 1  to SR 4  included in the input signal S in . 
     According to the phase control circuit  20 E in the present embodiment, similarly to the phase control circuit  20 B in the third embodiment, it is possible to reduce a loss of signals, and in addition, image signals can be reduced. 
     Seventh Embodiment 
       FIG.  14    is a diagram illustrating an example of a configuration of a phase control circuit  20 F according to a seventh embodiment of the disclosed technique. The phase control circuit  20 F is provided in correspondence with each of a plurality of antenna elements AN. The phase control circuit  20 F has a function for forming transmission beams B 1  to B 4  toward terminals  101  to  104  to transmit transmission signals and a function for forming reception beams to receive the signals transmitted from the terminals  101  to  104 . 
     The phase control circuit  20 F has a configuration corresponding to the phase control circuit  20  (refer to  FIG.  4   ) in the first embodiment and the phase control circuit  20 C ( FIG.  11   ) in the fourth embodiment. The phase control circuit  20 F includes a plurality of phase control units  40  and a plurality of mixer units  50 . Each of the plurality of phase control units  40  and each of the plurality of mixer units  50  are provided in correspondence with each of the transmission signals ST 1  to ST 4  and each of reception signals SR 1  to SR 4 . 
     In a case where the phase control circuit  20 F transmits a signal, each phase control unit  40  controls a phase of the transmission signal according to a transmission direction of the transmission signal. Each mixer unit  50  up-convers a frequency of the transmission signal of which the phase is controlled by the phase control unit. Each of the output signals of the plurality of mixer units are combined by a combining unit  60 , and an output signal S out  is generated. The output signal S out , is radiated via the antenna element AN to which correspond. 
     On the other hand, in a case where the phase control circuit  20 F receives signals, an input signal S in  obtained by combining the reception signals SR 1  to SR 4  transmitted from the terminals  101  to  104 , respectively is distributed to each mixer unit  50 . Each mixer unit  50  down-converts a frequency of the input signal S in  obtained by combining the plurality of reception signals SR 1  to SR 4 . Each phase control unit  40  changes a phase of the signal of which the frequency is down-converted by the corresponding mixer unit  50  according to an arrival direction of the reception signal. 
     The phase control circuit  20 F includes a transmission amplifier  91 A, a reception amplifier  91 B, and switches  92 A and  92 B between an input/output terminal  90  and the combining unit  60 . The transmission amplifier  91 A is enabled in a case of transmitting a signal and amplifies an amplitude of the output signal S out  output from the input/output terminal  90 . The reception amplifier  91 B is enabled in a case of receiving the signal and amplifies an amplitude of the input signal S in  input to the input/output terminal  90 . 
     Each of the switches  92 A and  92 B has a form of a Single-Pole Double-Throw (SPDT) switch and switches between a route through the transmission amplifier  91 A and a route through the reception amplifier  91 B. The switching of the switches  92 A and  92 B is controlled so that, in a case where a signal is transmitted, the route through the transmission amplifier  91 A is selected, and in a case where a signal is received, the route through the reception amplifier  91 B is selected. 
     In each phase control unit  40 , each of a first variable amplifier  420   a  and a second variable amplifier  420   b  Includes a transmission variable amplifier and a reception variable amplifier that are connected in parallel. In a case of transmitting a signal, the transmission variable amplifier is enabled, and in a case of receiving a signal, the reception variable amplifier is enabled. 
     According to the phase control circuit  20 F in the present embodiment, the mixer unit  50  and the phase control unit  40  are shared for signal transmission and signal reception. Therefore, a circuit size (occupied area of a circuit) can be reduced in comparison with a case where the mixer unit  50  and the phase control unit  40  are separately configured for transmission and for reception. Furthermore, the mixers included in the plurality of mixer units  50  share (interconnect) a local terminal to which the local signal LO is input and share (interconnect) an RF terminal to/from which an RF signal is input/output. As a result, the mixer unit  50  can be configured by, for example, a multi-finger type transistor, and it is possible to configure the mixer unit  50  to be exceedingly compact. Note that the first variable amplifier  420   a  and the second variable amplifier  420   b  can be arranged on either one the input sides and the output sides of a first phase switching unit  410   a  and a second phase switching unit  410   b.    
     Eighth Embodiment 
       FIG.  15 A  is a diagram illustrating an example of a configuration of a phase control circuit  20 G according to an eighth embodiment of the disclosed technique. The phase control circuit  20 G is provided in correspondence with each of a plurality of antenna elements AN. The phase control circuit  20 G has a function for forming transmission beams B 1  to B 4  toward terminals  101  to  104  to transmit transmission signals and a function for forming reception beams to receive the signals transmitted from the terminals  101  to  104 . The phase control circuit  20 G has a configuration corresponding to the phase control circuit  20 A (refer to  FIG.  9   ) in the second embodiment and the phase control circuit  20 D ( FIG.  12   ) in the fifth embodiment. 
     According to the phase control circuit  20 G in the present embodiment, a mixer unit and a phase control unit are shared for signal transmission and signal reception. Therefore, a circuit size can be reduced in comparison with a case where the mixer unit and the phase control unit are separately configured for transmission and for reception. Furthermore, according to the phase control circuit  20 G, image signals can be reduced. Furthermore, the first mixer  500   a  and the second mixer  500   b  share (interconnect) a local terminal to which the first local signal LO-I is input, and the third mixer  500   c  and the fourth mixer  500   d  share (interconnect) a local terminal to which the second local signal LO-Q is input. Moreover, the first to the fourth mixers  500   a  to  500   d  share (interconnect) an RF terminal to/from which an RF signal is input/output. 
       FIG.  15 B  is a diagram illustrating a case where each mixer in the phase control circuit  20 G illustrated in  FIG.  15 A  is configured by a transistor. Each mixer configured by a transistor  500  is a transistor shared for transmission and reception. Note that, in  FIG.  15 B , a bias circuit, a matching circuit, and the like are not illustrated. This type of mixer is called a resistive mixer (or switching mixer). A local signal is input to a gate of the transistor  500 . A drain (or source) of the transistor  500  is the RF terminal from which the RF signal is output. The source (or drain) of the transistor  500  is an IF terminal to which output signals of a first to a fourth variable amplifiers  420   a  to  420   d  are input. In each transistor  500 , potentials of the drain and the source are set to be the same in terms of a DC. This is the reason why this mixer is called a resistive mixer. A gate to which a first local signal LO-I is input is shared (interconnected), and a gate to which a second local signal LO-Q is input is shared (interconnected). The drain from which the RF signal is output is shared (Interconnected). The sources that are IF terminals separate from each other. In consideration of layout, this is a configuration in which only the sources are separated in a single-transistor layout including eight (or multiples of eight) gate fingers. The eight gate fingers can be used as a single circuit block, and the layout can be made exceedingly compact. 
     Ninth Embodiment 
       FIG.  16    is a diagram illustrating an example of a configuration of a phase control circuit  20 H according to a ninth embodiment of the disclosed technique. In  FIG.  17   , for easy understanding of the configuration, only a configuration portion related to one (IF 1 ) of signals (IF 1  to IF 4 ) in a baseband region or an intermediate frequency band used in the phase control circuit  20 H is illustrated.  FIG.  18 A to  18 D  are a table illustrating an example of an operation of the phase control circuit  20 H. Note that, in  FIGS.  16  to  18 D , an RF-P, an RF-I, and an RF signals correspond to the output signal S out  or the input signal S in  described above. Furthermore, an IF 1 -I to an IF 4 -I, an IF 1 -Q to an IF 4 -Q, and IF signals correspond to the above-described transmission signals ST 1  to ST 4  or the reception signals SR 1  to SR 4 . 
     The phase control circuit  20 H is provided in correspondence with each of a plurality of antenna elements AN. The phase control circuit  20 H in the present embodiment has a function for forming transmission beams B 1  to B 4  toward terminals  101  to  104  to transmit transmission signals and a function for forming reception beams to receive the signals transmitted from the terminals  101  to  104 . 
     In addition, the phase control circuit  20 H has a single-balanced configuration that differentially inputs two local signals of which phases are orthogonal to each other, differentially inputs/outputs signals in an RF band, and inputs/outputs signals in the baseband region or the intermediate frequency band in a single-ended manner. A positive phase signal LO-I-P of a first local signal LO-I has a phase difference of 0° with respect to a reference phase, and a reverse phase signal LO-I-M of the first local signal LO-I has a phase difference of 180° with respect to the reference phase. A positive phase signal LO-Q-P of a second local signal LO-Q has a phase difference of 90° with respect to the reference phase, and a reverse phase signal LO-Q-M of the second local signal LO-Q has a phase difference of −90° with respect to the reference phase. Furthermore, the positive phase signal RF-I and a reverse phase signal RF-M in the RF band are output at the time of transmission and are input at the time of reception. Furthermore, each of the positive phase signals IF 1 -I to IF 4 -I and the quadrature signals IF 1 -Q to IF 4 -Q in the baseband region or the intermediate frequency band are input in a single-ended manner at the time of transmission and are output in a single-ended manner at the time of reception. 
     According to the phase control circuit  20 H, it is possible to reduce a loss of signals while suppressing an increase in a circuit size (occupied area of circuit), and in addition, image signals can be reduced. Furthermore, by differentially inputting the local signal to be input to a mixer unit  50 , resistance to an exogenous common mode (same phase mode) noise is improved, and leakage of the local signal to the RF terminal can be suppressed. Note that a first to a fourth variable amplifiers  420   a  to  420   d  can be arranged on either one of the input sides and the output sides of a first to a fourth phase switching units  410   a  to  410   d.    
     In the phase control circuit  20 H, a local terminal of each mixer to which the local signal LO-I-P is input is shared (interconnected), and a local terminal of each mixer to which the local signal LO-I-M is input is shared (interconnected). Furthermore, a local terminal of each mixer to which the local signal LO-Q-P is input is shared (interconnected), and a local terminal of each mixer to which the local signal LO-Q-M is input is shared (interconnected). Furthermore, an RF terminal of the mixer to/from which the RF signal RF-P is input/output is shared (interconnected), and an RF terminal of the mixer to/from which the RF signal RF-M is input/output is shared (interconnected). As a result, the mixer unit can be configured by, for example, a multi-finger type transistor, and it is possible to configure the mixer unit to be exceedingly compact. 
     The operation table illustrated in  FIG.  18 A to  18 D  is written as focusing on a single IF signal. An example (U1, U2, U3, or U4) of four phase states (one for each of four quadrants) and a switching setting example of a phase switching unit are written. Furthermore, a case where amplification rates of two variable amplifiers that amplify signals orthogonal to each other are made to be the same is illustrated. The following content is described in each column indicated by column numbers [1] to [17] in the operation table in  FIG.  18 A to  18 D . 
     [1] Output phase state of RF signal (at the time of transmission), four types (one for each quadrant), equivalent to (+45°, +135°, −45°, and −135°), (equivalent to output phase state of IF signal at the time of reception) 
     [2] Identification symbol of unit mixer (or mixer transistor) 
     [3] Input phase of local signal (LO signal) to unit mixer 
     [5] Phase inversion state of LO signal (1: non-inversion, −1: inversion) Note that, since this is an example in the embodiment in which quadrant is not switched with LO signal, only non-conversion is used. 
     [6] Input phase of IF signal to unit mixer (at the time of transmission) or output phase from unit mixer (at the time of reception) 
     [8] Phase inversion state of IF signal (0/n switching by phase switching unit, 1: non-inversion, −1: inversion) 
     [9] Phase inversion switch grouping of IF signal (grouping when quadrant is switched (grouping into two groups), performing phase switching for each group at once) 
     [10] Phase of upper sideband of RF signal (RF terminal position of unit mixer) 
     [11] Phase of lower sideband of IRF signal (RF terminal position of unit mixer) 
     [12] Phase of RF signal at the time of synthesis (transmission) or distribution (reception) (1: in-phase synthesis (distribution), −1: reverse-phase synthesis (distribution)) 
     [13] Phase of leaked LO signal (RF terminal position of unit mixer) 
     [14] RF output phase (at the time of transmission), IF signal output phase (at the time of reception) 
     [15] RF upper sideband amplitude (at the time of transmission . . . 1: signal is output, 0: signal is not output (image rejection), at the time of reception . . . 1: signal is received, 0: signal is not received (image rejection)) 
     [16] RF lower sideband amplitude (at the time of transmission . . . 1: signal is output, 0: signal is not output (image rejection), at the time of reception . . . 1: signal is received, 0: signal is not received (image rejection)) Note that, in the example of the operation description table in the embodiment, the lower sideband is set to be image-rejected. 
     [17] LO signal leakage to RF terminal (0: LO signal is canceled through RF synthesis (distribution) unit, 0: LO signal is not canceled) Note that, in the embodiment, the LO signal is canceled. 
     The method for selecting the upper sideband and the lower sideband of the image rejection is performed by referring to grouping in the column [4] or column [7]. 
     [4] LO signal inversion RF sideband grouping (classify into group g and group h) 
     [7] IF signal inversion RF sideband grouping (classify into group e and group f) LO signal phase inversion of group h (or group g) or IF signal phase (re)inversion of group f (or group e). For example, for a unit mixer of the IF signal phase inversion group e, if all the IF signals in the group f are further inverted with respect to the phase inversion (non-inversion) of the IF signal, another sideband is rejected. 
     Tenth Embodiment 
       FIG.  19    is a diagram illustrating an example of a configuration of a phase control circuit  20 I according to a tenth embodiment of the disclosed technique. In  FIG.  20   , for easy understanding of the configuration, only a configuration portion related to one (IF 1 ) of signals (IF 1  to IF 4 ) in a baseband region or an intermediate frequency band used in the phase control circuit  20 I is illustrated.  FIG.  21 A to  21 D  are a table illustrating an example of an operation of the phase control circuit  20 I. Note that, in  FIGS.  19  to  21 D , an RF and an RF signal correspond to the above-described output signal S out  or the input signal S in . Furthermore, an IF 1 -I to an IF 4 -I, an IF 1 -Q to an IF 4 -Q, and IF signals correspond to the above-described transmission signals ST 1  to ST 4  or the reception signals SR 1  to SR 4 . 
     The phase control circuit  20 I is provided in correspondence with each of a plurality of antenna elements AN. The phase control circuit  20 I according to the present embodiment has a function for forming transmission beams B 1  to B 4  toward terminals  101  to  104  to transmit transmission signals and a function for forming reception beams to receive the signals transmitted from the terminals  101  to  104 . 
     In addition, the phase control circuit  20 I has a single-balanced configuration that differentially inputs two local signals of which phases are orthogonal to each other, inputs/outputs signals in an RF band in a single-ended manner, and differentially inputs/outputs signals in the baseband region or the intermediate frequency band. A positive phase signal LO-I-P of a first local signal LO-I has a phase difference of 0° with respect to a reference phase, and a reverse phase signal LO-I-M of the first local signal LO-I has a phase difference of 180° with respect to the reference phase. A positive phase signal LO-Q-P of a second local signal LO-Q has a phase difference of 90° with respect to the reference phase, and a reverse phase signal LO-Q-M of the second local signal LO-Q has a phase difference of −90° with respect to the reference phase. The signal RF in the RF band is output in a single-ended manner at the time of transmission and is input in a single-ended manner at the time of reception. Furthermore, the in-phase signals IF 1 -I to IF 4 -I and the quadrature signals IF 1 -Q to IF 4 -Q in the baseband region or the intermediate frequency band are each differentially input at the time of transmission and is differentially output at the time of reception. 
     According to the phase control circuit  20 I, it is possible to reduce a loss of signals while suppressing an increase in a circuit size (occupied area of circuit), and in addition, image signals can be reduced. Furthermore, by differentially inputting the local signal to be input to a mixer unit  50 , resistance to an exogenous common mode (same phase mode) noise is improved, and leakage of the local signal to an RF terminal can be suppressed. 
     In the phase control circuit  20 I, a local terminal of each mixer to which the local signal LO-I-P is input is shared (interconnected), and a local terminal of each mixer to which the local signal LO-I-M is input is shared (interconnected). Furthermore, a local terminal of each mixer to which the local signal LO-Q-P is input is shared (interconnected), and a local terminal of each mixer to which the local signal LO-Q-M is input is shared (interconnected). Furthermore, the RF terminal of the mixer to/from which the RF signal is input/output is shared (interconnected). As a result, the mixer unit can be configured by, for example, a multi-finger type transistor, and it is possible to configure the mixer unit to be exceedingly compact. 
     Eleventh Embodiment 
       FIG.  22 A to  22 C  are diagrams illustrating an example of a configuration of a phase control circuit  20 J according to an eleventh embodiment of the disclosed technique. In  FIG.  23   , for easy understanding of the configuration, only a configuration portion related to one (IF 1 ) of signals (IF 1  to IF 4 ) in a baseband region or an intermediate frequency band used in the phase control circuit  20 J is illustrated.  FIG.  24 A to  24 G  are a table illustrating an example of an operation of the phase control circuit  20 ). Note that, in  FIGS.  22 A to  24 G , an RF and an RF signal correspond to the above-described output signal S out  or the input signal S in . Furthermore, an IF 1 -I to an IF 4 -I, an IF 1 -Q to an IF 4 -Q, and IF signals correspond to the above-described transmission signals ST 1  to ST 4  or the reception signals SR 1  to SR 4 . 
     The phase control circuit  203  is provided in correspondence with each of a plurality of antenna elements AN. The phase control circuit  203  has a function for forming transmission beams B 1  to B 4  toward terminals  101  to  104  to transmit transmission signals and a function for forming reception beams to receive the signals transmitted from the terminals  101  to  104 . 
     In addition, the phase control circuit  203  has a double-balanced configuration that differentially inputs two local signals of which phases are orthogonal to each other, differentially inputs/outputs signals in an RF band, and differentially inputs/outputs signals in the baseband region or the intermediate frequency band. A positive phase signal LO-I-P of a first local signal LO-I has a phase difference of 0° with respect to a reference phase, and a reverse phase signal LO-I-M of the first local signal LO-I has a phase difference of 180° with respect to the reference phase. A positive phase signal LO-Q-P of a second local signal LO-Q has a phase difference of 90° with respect to the reference phase, and a reverse phase signal LO-Q-M of the second local signal LO-Q has a phase difference of −90° with respect to the reference phase. Furthermore, the positive phase signal RF-I and a reverse phase signal RF-M in the RF band are output at the time of transmission and are input at the time of reception. Furthermore, the positive phase signals IF 1 -I to IF 4 -I and the quadrature signals IF 1 -Q to IF 4 -Q in the baseband region or the intermediate frequency band are differentially input at the time of transmission and is differentially output at the time of reception, respectively. 
     According to the phase control circuit  20 J, it is possible to reduce a loss of signals while suppressing an increase in a circuit size (occupied area of circuit), and in addition, image signals can be reduced. Furthermore, by differentially inputting the local signal to be input to a mixer unit  50 , resistance to an exogenous common mode (same phase mode) noise is improved, and leakage of the local signal to an RF terminal can be suppressed. 
     In the phase control circuit  20 J, a local terminal of each mixer to which the local signal LO-I-P is input is shared (interconnected), and a local terminal of each mixer to which the local signal LO-I-M is input is shared (interconnected). Furthermore, a local terminal of each mixer to which the local signal LO-Q-P is input is shared (interconnected), and a local terminal of each mixer to which the local signal LO-Q-M is input is shared (interconnected). Furthermore, an RF terminal of the mixer to/from which the RF signal RF-P is input/output is shared (interconnected), and an RF terminal of the mixer to/from which the RF signal RF-M is input/output is shared (interconnected). As a result, the mixer unit can be configured by, for example, a multi-finger type transistor, and it is possible to configure the mixer unit to be exceedingly compact. 
     Note that, as illustrated in  FIG.  25   , the phase control circuit  20 J may have a configuration in which two mixers share a phase switching unit. With this configuration, an effect of suppressing an increase in a circuit size (occupied area of a circuit) is promoted. 
     With respect to the above first to eleventh embodiments, the following supplementary notes are further disclosed. 
     All examples and conditional language provided herein are intended for the pedagogical purposes of aiding the reader in understanding the invention and the concepts contributed by the inventor to further the art, and are not to be construed as limitations to such specifically recited examples and conditions, nor does the organization of such examples in the specification relate to a showing of the superiority and inferiority of the invention. Although one or more embodiments of the present invention have been described in detail, it should be understood that the various changes, substitutions, and alterations could be made hereto without departing from the spirit and scope of the invention.