Patent Publication Number: US-9407171-B2

Title: Apparatus and a method for enhancing power output in electrical circuits

Description:
CROSS-REFERENCE TO RELATED APPLICATION 
     This application is the U.S. national stage of International (PCT) Patent Application No. PCT/SG2012/000314, which was filed on Sep. 3, 2012, and the contents of which are hereby incorporated herein by reference in their entirety. 
     FIELD OF THE INVENTION 
     The present invention relates to an apparatus and a method for enhancing power output, for example, during Direct Current (DC) to Alternating Current (AC) conversion. 
     BACKGROUND 
     Certain types of distributed power generators supplying DC power provide unstable voltages. An example would be a power generator dependent on solar power. Hence, in the design of the circuitries to convert the DC power supplied by such power generators into AC power, one would have to take into account the unstable voltages. 
     DC to AC converter circuits typically include controller components, such as a pulse width modulation (PWM) based controller, power electronic switches and capacitors. Various DC to AC converter circuit configurations may also include full-bridge or half-bridge inverters. The use of such electronic components can help to compensate for the unstable voltages supplied by the power generator. 
     However, current DC to AC inverter circuits have a few drawbacks. For instance, DC to AC inverter circuits used for power generators relying on solar panels have high power transmission losses in the connecting lines between the panels. External power sources may also be required to operate certain components of the DC to AC inverter circuits. The DC to AC inverter circuits are also bulky in size and may include big transformer windings with high heat losses. In addition, power electronic switches used in current DC to AC inverter circuits have switching losses and they could be exacerbated by poor design of the DC to AC inverter circuits, which is the case for some existing designs of DC to AC inverter circuits. Moreover, the DC to AC inverter circuits would not work without auxiliary power source from a battery or grid power if voltage from the power source, e.g. solar panels is not constant. 
     In addition, current technology used in On-Grid Photovoltaic systems has inherent problems in residential and commercial usage. For instance, the absence of safety features poses risks to both workers installing or maintaining the system, and to fire-fighters dealing with fires in the vicinity of photovoltaic installations. 
     Therefore, it is important to design a well-calibrated DC to AC inverter for power generators supplying DC power to reduce amongst other things overall heat losses, transmission losses, switching losses and conversion losses. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       Various embodiments of the invention will now be described, by way of example only, and with reference to the accompanying drawings in which: 
         FIG. 1  is a block diagram of a DC to AC power enhancer system. 
         FIG. 2A  is a circuit diagram of a DC voltage booster processing system. 
         FIG. 2B  is a detailed circuit diagram of a DC voltage booster. 
         FIG. 3A  is a circuit diagram of a DC to AC conversion process. 
         FIG. 3B  is a circuit diagram of a microcontroller circuit of the DC to AC conversion process. 
         FIG. 4  is a circuit diagram of an AC power booster. 
         FIG. 5  shows a flowchart illustrating steps taken at the DC booster processing system. 
         FIG. 6  shows a flowchart illustrating steps taken at the DC voltage booster. 
         FIG. 7  shows a flowchart illustrating steps taken at the DC to AC Conversion process. 
         FIG. 8  shows a flowchart illustrating steps taken at the AC power booster. 
         FIG. 9  is a chart illustrating voltage profiles at specific points in the DC voltage booster. 
         FIG. 10  is a chart illustrating voltage profiles at specific points in the AC power booster. 
         FIG. 11  illustrates waveforms produced after triggering Insulated gate Bipolar Transistors. 
         FIG. 12  illustrates waveforms produced after triggering Insulated gate Bipolar Transistors. 
     
    
    
     SUMMARY OF THE INVENTION 
     In accordance with one aspect of the present invention, there is provided an apparatus for enhancing power output, the apparatus comprising: a thyristor having an anode, a cathode and a gate; and a controller connected to the gate, the cathode and the anode, wherein, when the anode is provided with a voltage, the controller is configured for activating the thyristor to allow current flow between the anode and the gate in a first instance and is configured for activating the thyristor to allow current flow between the gate and the cathode in a second instance so as to provide the cathode with an enhanced voltage, the enhanced voltage being an enhancement of the voltage at the anode. 
     The controller may activate the thyristor to allow current flow between the anode and the gate in the first instance through a regulating signal and the regulating signal comprising: a first time period having a pulsating wave; and a second time period with voltage rising to the voltage at the anode. 
     The regulating signal may comprise a third time period having a voltage dropping from the voltage at the anode to a lower voltage; and a fall in voltage to the lower voltage value lasting a fourth time period during the third time period so as to activate the thyristor to allow current flow between the gate and the cathode in the second instance. 
     Time difference between the first instance and the second instance may be in order of microseconds, or shorter to an extent that would still provide the enhanced voltage at the cathode. 
     The apparatus may comprise a capacitor arranged at the gate to supplement the voltage at the cathode. 
     The apparatus may comprise a Direct Current (DC) source, and a switch for switching the switch to lead current from the DC source to the anode when the controller detects that voltage of the DC source is below a threshold value, and for switching the switch to lead current to an output terminal connected to the cathode when the controller detects that voltage of the DC source is above the threshold value. 
     The apparatus may comprise one or more capacitors arranged in parallel to the switch, the controller being configured to enable current discharged from the one or more capacitors to flow to the switch if the voltage of the DC source is below the threshold value. 
     The apparatus may comprise one or more Insulated Gate Bipolar Transistor (IGBT) controlled by the controller to convert the voltage at the cathode into an Alternating Current (AC) signal, wherein the controller is configured for detecting energy loss caused by the one or more IGBT and for adjusting a compensation circuit to compensate the energy loss based on the energy loss detected. 
     The apparatus may comprise one or more resistors arranged between the cathode and the anode for adjusting resistance. 
     The controller may be configured for monitoring voltage at the anode or the cathode for leading current at the respective anode or cathode to the one or more resistors based on the monitored voltage. 
     The apparatus may comprise one or more resistors arranged between the cathode and the anode and between the anode and the gate for adjusting resistance at the cathode. 
     The controller may be configured for monitoring resistance value at the anode, the gate or the cathode for leading current at the respective anode, gate or cathode to the one or more resistors based on the monitored resistance value. 
     The controller may be configured for monitoring voltage at the anode of the thyristor for leading current to a diode based on the monitored voltage, the diode comprising with a diode anode for receiving current from the anode of the thyristor and a diode cathode connected to the gate of the thyristor. 
     The controller may activate the thyristor to allow current at the cathode to increase by 1% through the regulating signal prior to an increase of voltage at the cathode to the enhanced voltage. 
     The apparatus may comprise a second thyristor comprising: an anode for receiving the enhanced voltage; a gate for connecting to a load; and a cathode for connecting to the load. 
     The controller may activate the thyristor to allow current flow between the anode and the gate in the first instance until resistance value calculated at the anode is similar to resistance value calculated at the gate for a first time period. 
     The controller may activate the thyristor to allow current flow between the gate and the cathode in the second instance until resistance value calculated at the anode is similar to resistance value calculated at the cathode for a second time period. 
     The second period may be longer than the first period. 
     The controller may activate the thyristor to allow current flow between the anode and the gate in the first instance until voltage at the anode is similar to voltage at the gate for a first time period. 
     The controller may activate the thyristor to allow current flow between the gate and the cathode in the second instance until voltage at the anode is similar to voltage at the cathode for a second time period. 
     The second period may be longer than the first period. 
     The regulating signal may comprise a fifth time period having a voltage rising from a negative peak voltage to zero voltage; and a rise in voltage lasting a sixth time period during the fifth time period so as to activate the thyristor to allow current flow between the anode and the gate in the first instance. 
     In accordance with another aspect of the present invention, there is provided a method for enhancing power output of an apparatus comprising a thyristor having an anode, a cathode and a gate, the anode being provided with a voltage, the method comprising: activating the thyristor to allow current flow between the anode and the gate in a first instance; and activating the thyristor to allow current flow between the gate and the cathode in a second instance, so as to provide the cathode with an enhanced voltage, the enhanced voltage being an enhancement of the voltage at the anode. 
     The method may comprise activating the thyristor to allow current flow between the anode and the gate in the first instance through a regulating signal, the regulating signal comprising: a first time period having a pulsating wave; and a second time period with voltage rising to the voltage at the anode. 
     The regulating signal may comprise a third time period having a voltage dropping from the voltage at the anode to a lower voltage; and a fall in voltage to the lower voltage value lasting a fourth time period during the third time period so as to activate the thyristor to allow current flow between the gate and the cathode in the second instance. 
     Time difference between the first instance and the second instance may be in order of microseconds, or shorter to an extent that would still provide the enhanced voltage at the cathode. 
     The method may comprise supplementing voltage at the cathode with current discharged from a capacitor arranged at the gate. 
     The method may comprise switching a switch to lead current from a DC source to the anode when the controller detects that voltage of the DC source is below a threshold value; and switching a switch to lead current to an output terminal connected to the cathode when the controller detects that voltage of the DC source is above the threshold value. 
     The method may comprise enabling current discharged from one or more capacitors arranged in parallel to the switch to flow to the switch if the voltage of the DC source is below the threshold value. 
     The method may comprise converting voltage at the cathode into an Alternating Current (AC) signal using one or more Insulated Gate Bipolar Transistor (IGBT) controlled by the controller; detecting energy loss caused by the one or more IGBT; and adjusting a compensation circuit to compensate the energy loss based on the energy loss detected. 
     The method may comprise adjusting resistance using one or more resistors arranged between the cathode and the anode. 
     The method may comprise leading current at the anode or the cathode to the one or more resistors based on voltage monitored voltage at the respective anode or cathode. 
     The method may comprise adjusting resistance using one or more resistors arranged between the cathode and the anode and between the anode and the gate. 
     The method may comprise leading current at the anode, the gate or the cathode to the one or more resistors based on monitored resistance value at the respective anode, gate or cathode. 
     The method may comprise monitoring voltage at the anode of the thyristor for leading current to a diode based on the monitored voltage, the diode comprising with a diode anode for receiving current from the anode of the thyristor and a diode cathode connected to the gate of the thyristor. 
     The method may comprise activating the thyristor to allow current at the cathode to increase by 1% through the regulating signal prior to an increase of voltage at the cathode to the enhanced voltage. 
     The method may comprise leading current to an anode of a second thyristor from the cathode of the thyristor to apply the enhanced voltage to the anode of the second thyristor, a gate and a cathode of the second thyristor being connected to a load. 
     The method may comprise activating the thyristor to allow current flow between the anode and the gate in the first instance until resistance value calculated at the anode is similar to resistance value calculated at the gate for a first time period. 
     The method may comprise activating the thyristor to allow current flow between the gate and the cathode in the second instance until resistance value calculated at the anode is similar to resistance value calculated at the cathode for a second time period. 
     The second period may be longer than the first period. 
     The method may comprise activating the thyristor to allow current flow between the anode and the gate in the first instance until voltage at the anode is similar to voltage at the gate for a first time period. 
     The method may comprise activating the thyristor to allow current flow between the gate and the cathode in the second instance until voltage at the anode is similar to voltage at the cathode for a second time period. 
     The second period may be longer than the first period. 
     The regulating signal may comprise a fifth time period having a voltage rising from a negative peak voltage to zero voltage; and a rise in voltage lasting a sixth time period during the fifth time period so as to activate the thyristor to allow current flow between the anode and the gate in the first instance. 
     DETAILED DESCRIPTION 
       FIG. 1  is a block diagram of a DC to AC power enhancer system  100 . It is appreciated that the DC to AC power enhancer system  100  could be implemented as an apparatus, or more specifically, a circuit board. The power enhancer system  100  accepts DC input power from a DC source  101  (also known as DC input source) and supplies AC output power. The DC source  101  may for instance be a distributed power generator relying on solar power or any other DC sources such as batteries, wind turbines, hydro-turbines, ultra-capacitors and any other Direct Current power source. 
     The power enhancer system  100  comprises a DC voltage booster subsystem  200 , a DC to AC conversion sub-system  300  and an AC power booster subsystem  400 . 
     The DC voltage booster processing system  200  comprises a DC voltage booster  202  that is connected to a microcontroller  211 . The DC voltage booster processing system  200  takes its input from the DC source  101  whose voltage can fluctuate, typically between 12 to 45 Volts for a distributed power generator relying on solar power. The DC voltage booster  202  supplies a DC voltage of a particular waveform to the DC to AC conversion subsystem  300 , in accordance to conversion and switching control signals received from the microcontroller  211 . The DC voltage booster processing system  200  is used to enhance and stabilize the DC output voltages from the DC source  101 . By regulating the DC output voltages from the DC source  101 , more accurate DC to AC conversion can be performed by the DC to AC conversion subsystem  300 . 
     The DC to AC conversion subsystem  300  comprises a DC to AC converter  301  and a microcontroller  311 . In other examples, the microcontroller  311  and the microcontroller  211  could be one and the same physical microcontroller. The same physical microcontroller could have separate input and output pins for the operations of the microcontroller  311  and run separate logical algorithms from that of the microcontroller  211 . The DC to AC converter  301  takes its input from the output of the DC voltage booster  201 . The DC to AC converter  301  is further coupled to the microcontroller  311  and supplies an AC voltage to the AC power booster subsystem  400  in accordance to conversion and switching control signals received from the microcontroller  311 . 
     The AC power booster subsystem  400  comprises an AC power booster  401  that is connected to a microcontroller  411 . In other examples, the microcontroller  411 , the microcontroller  211  and/or the microcontroller  311  could be one and the same physical microcontroller. The same physical microcontroller could have separate input and output pins for the operations of microcontrollers  211  and/or the microcontroller  311 , and run separate logical algorithms from that of the microcontroller  211  and/or the microcontroller  311 . The AC power booster  401  takes its input from the output of the DC to AC converter  301 . The AC power booster  401  is further coupled to the microcontroller  411  and supplies enhanced AC power to one or more connected loads  102  in accordance to conversion and switching control signals received from the microcontroller  411 . The AC power booster  401  outputs an AC voltage that is stable and usable by the one or more connected loads  102 . 
     It is appreciated that in other examples, there could be just one microcontroller operating the functions of the microcontrollers  211 ,  311  and/or  411 . For simplicity, in the illustrations as follows, the use of one microcontroller  211  to carry out the functions of the three microcontrollers (i.e.  211 ,  311  and  411 ) as discussed would be described. 
     The words ‘boost’ and ‘booster’ are used interchangeably with the words ‘enhance’ and ‘enhancer’ respectively. It is appreciated that voltage or power enhancement does not necessarily mean providing increased voltage and/or current. It covers enhancement on the power output to provide sufficient drive at a specific voltage and/or current to, for instance, support more loads. Providing sufficient drive may not necessarily involve increased voltage or current. Enhancement by providing increased voltage is illustrated by the DC voltage booster  202 . Enhancement by providing sufficient drive for more loads is illustrated by the AC power booster  401 . 
       FIG. 2A  is an example of the circuit diagram of the DC voltage booster subsystem  200  in  FIG. 1 . The DC input source  101  in  FIG. 1  is connected to two capacitors  203 , the microcontroller  211  and a circuit juncture  212  through a fuse  240 , which provides overcurrent protection. The DC input source  101  provides current to a diode  281  having its diode cathode end connected to the microcontroller  211 . The diode  281  adjusts the current flow to the microcontroller  211  to provide a stable power supply of, for instance, 2 to 5 Volts for the microcontroller  211  to operate. Furthermore, the circuit juncture  212  is connected to a circuit juncture  222 . Both circuit junctures  212  and  222  are individually connected to the microcontroller  211 . 
     It is appreciated that in  FIGS. 2A, 2B and 4 , the same microcontroller  211  is drawn at each circuit juncture of interest to illustrate its connection to the respective circuit junctures. 
     At circuit juncture  212 , the microcontroller  211  has one ‘R’ pin for regulating current/voltage and two ‘M’ pins for monitoring current/voltage connected to corresponding circuit points  251 ,  252  and  253 . Circuit point  251  is in turn connected to the DC input source  101  through the fuse  240 . Circuit point  252  is connected to the capacitors  203  and circuit point  253  is connected to point  254  of circuit juncture  222 . 
     The ‘M’ pin connected to point  251  monitors incoming DC voltage values from the DC input source  101  after going through the fuse  240 . When the DC voltage monitored at point  251  is greater than or equal to, in this example, 35 Volts, the ‘R’ pin connected to point  212  enables current to flow from points  251  to  253  through the microcontroller  211  and from points  251  to  252  through the microcontroller  211  to charge the capacitors  203 . When the DC voltage monitored at point  251  is lesser than, in this example, 35 Volts, the ‘R’ pin enables current to flow from points  251  to  252  and from points  252  to  253  through the microcontroller  211  to allow the capacitors  203  to discharge 
     At circuit juncture  222 , the microcontroller  211  has two ‘R’ pins for regulating current/voltage and one ‘M’ pin for monitoring current/voltage connected to corresponding circuit points  254 ,  255  and  256 . Circuit point  254  is in turn connected to point  253  of circuit juncture  212 . Circuit point  255  is connected to input B  226  of the internal distribution point  221 . Circuit point  256  is connected to input point A  224  of the internal distribution point  221 . 
     The ‘M’ pin connected to point  254  monitors voltage value at point  254 , which have the same voltage value as point  253 . If the voltage value at point  254  is between a certain range, in this example, 12 to 34 Volts, current is enabled to flow from points  254  to  256 . If voltage value at point  254  is greater than or equal to, in this example, 35 Volts, current is enabled to flow from points  254  to  255 . 
     The ‘R’ pins connected at circuit junctures  212  and  222  are configured to help regulate the current flow and voltage at the various circuit junctures and the ‘M’ pins connected at circuit junctures  212  and  222  are configured for monitoring the voltage and current values at the respective circuit junctures. 
     The internal distribution point  221  is a switch that is connected to the microcontroller  211 . The internal distribution point  221  has two inputs A  224  and B  226  and two outputs C  228  and D  230 . The circuit juncture  222  splits into two separate lines i.e. through points  256  and  255  that are each connected to the input A  224  and the input B  226  of the internal distribution point  221  respectively. The output C  228  of the internal distribution point  221  is coupled to an input of a DC voltage booster  202 . An output of the DC voltage booster  202  is connected to a circuit juncture  214 . The output D  230  of the internal distribution point  221  is connected to the output of the DC voltage booster  202  at the circuit juncture  214 . The switching of the internal distribution point  221  is controlled via the 3 pins of the microcontroller  211  that are connected to points  254 ,  255  and  256 . 
     The DC voltage booster  202  is connected to ground at a circuit point  215 . The circuit point  215  is coupled to a ground point (i.e. negative terminal) of a terminal block  204 . The output of the DC voltage booster  202  is also connected to the terminal block  204  through the circuit juncture  214 . The circuit juncture  214  is connected to a positive terminal  223  of the terminal block  204  to provide the boosted DC voltage provided by the DC Voltage booster  202 , if necessary. 
     To illustrate the voltage enhancing ability of the DC voltage booster subsystem  200 , a case where the DC input source  101  is a solar panel providing an unstable supply of 12 to 45 Volts, and the DC voltage booster subsystem  200  is to obtain a stable DC supply of 35 Volts by boosting the unstable supply of 12 to 45 Volts from the DC input source  101  is considered as follows. For the unstable supply of 12 to 45 Volts, the rating of the fuse  240  could be set as 45 Volts or higher. 
     The microcontroller  211  controls the connection patches in the internal distribution point  221  according to the following steps. Where the DC input source  101 , coupled to the capacitor  203  is monitored to be stable at or higher than a preset desired voltage reference ( 213  in  FIG. 2A ), in this case, 35 Volts, the microcontroller releases the voltage energy in capacitor  203  by patching the circuit juncture  212  through to circuit juncture  214 . When the microcontroller  211  senses the DC input source  101  is less than the preset desired voltage reference ( 213  in  FIG. 2A ) (35 Volts), the patch at the internal distribution point  221  between circuit junctures  212  and  214  will be broken. Rather, the weaker DC source voltage will be released to the DC voltage booster  202  for boosting by patching the internal distribution point  221  accordingly. 
     With regard to the input A  224  of the internal distribution point  221 , if the microcontroller  211  determines the voltage at the circuit juncture  222  via the ‘M’ pin connected to point  254  to be between 12-34 Volts, the microcontroller  211  would control the internal distribution point  221  to patch input A  224  to the output C  228 . After patching input A  224  to the output C  228 , the DC voltage booster  202  would receive the voltage at the circuit juncture  222  of between 12-34 Volts and would be activated to provide a boost to the 12-34 Volts to try and achieve the desired 35 Volts DC output at the circuit juncture  214 . 
     With regard to input B  226  of the internal distribution point  221 , if the microcontroller  211  determines that the voltage at the circuit juncture  222  is between 12-34 Volts and determines that charge is available at the capacitors  203 , the microcontroller  211  would control the internal distribution point  221  to patch input B  226  to the output D  230  so that the charge in the capacitors  203  would be drawn through input B  226  and be directed to the output D  230 . The necessary controlling would be done by the microcontroller  211  via the 3 pins connected to  251 ,  252  and  253  and the 3 pins connected to points  254 ,  255  and  256  to enable the charge in the capacitors  203  to be drawn through input B  226  to be directed to the output D  230 . The microcontroller  211  determines whether charge is available at the capacitors  203  by monitoring the Voltage level at circuit juncture  212  via one or both of the ‘M’ pins connected to points  251  and  253 . 
     The microcontroller  211  is configured to monitor circuit juncture  212  for the flow of the supply and check the condition whether the voltage is equal to or greater than 35 Volts. If the voltage is equal or greater to 35 Volts as determined via one or both of the ‘M’ pins connected to points  251  and  253  at circuit juncture  212 , the capacitors would be charged. If not, the microcontroller  211  would start to monitor the circuit juncture  222 . 
     At circuit juncture  222 , the microcontroller  211  checks whether backup charge is available at the capacitors  203  when the Voltage at circuit juncture  222  is detected to be lesser than 35 Volts via the ‘M’ pin connected to point  254 . If backup charge is available at the capacitors  203 , it will withdraw charge from the capacitors  203  to release the required voltage. Otherwise, the microcontroller  211  will patch input A  224  to the output C  228  to direct the voltage of lesser than 35 Volts at circuit juncture  222  to the DC Voltage booster for boosting. Whether backup charge is available or not can be deduced via one or more of the microcontroller pins connected to points  251 ,  252  and  253  of the circuit juncture  212 . 
     More details to obtain the preset desired voltage reference ( 213  in  FIG. 2A ) through the DC voltage booster subsystem  200  of, in this case, 35 Volts is provided as follows with reference to  FIG. 5 . 
       FIG. 5  shows a flowchart illustrating the steps taken to provide the DC boosting provided by the DC conversion sub-system  200 . In this instance, a stable DC output of 35 Volts is to be obtained from the DC input source  101 , which is providing DC Voltage fluctuating between 12 and 45 Volts. Reference is made to components in  FIGS. 2A and 2B . 
     At step  501 , the microcontroller  211  monitors the fluctuating DC input source  101  at circuit juncture  212  via one or both the ‘M’ pins connected to points  251  and  253  in  FIG. 2A . 
     At step  502 , the microcontroller  211  checks if the Voltage of the DC input source  101 , Vdc, is greater than or equal to a predetermined 35 Volts at circuit juncture  212  via one or both the ‘M’ pins connected to points  251  and  253  in  FIG. 2A . 
     If Vdc is greater than or equal to 35 Volts at step  502 , the microcontroller  211  enables the voltage energy of the Vdc that is greater than 35 Volts to be stored into the capacitors  203  at step  503  via one or more of the pins connected to points  251 ,  252  and  253  in  FIG. 2A  and at the same time releases the voltage energy of Vdc in the capacitors  203  by patching the circuit juncture  212  through to circuit juncture  214  i.e. patching input B  226  to the output D  230  in  FIG. 2A  at step  504  and disconnecting input A  224  to the output C  228  in  FIG. 2A . After step  504 , the circuit juncture  214  would provide a DC output of 35 Volts at circuit juncture  214  in  FIG. 2A  and this output would be channeled to the next stage for further processing at step  505 . 
     If Vdc is lesser than 35 Volts at step  502 , the microcontroller  211  would check and look for back up charge supply from the capacitors  203  at step  506  via one or more of the pins connected to points  251 ,  252  and  253  in  FIG. 2A . 
     After step  506 , the microcontroller  211  checks at circuit juncture  222 , via one or more of the pins connected to points  254 ,  255  and  256  in  FIG. 2A , if the back up Voltage supply at the capacitors  203 , Vdc (backup), is greater than 35 Vdc at step  507 . 
     If Vdc (backup) is greater than or equal to 35 Volts at step  507 , the microcontroller would, via control of one or more of the pins connected to points  251 ,  252 ,  253 ,  254 ,  255  and  266  in  FIG. 2A , withdraw the voltage energy from the capacitors  203  at step  508  and release the voltage energy of Vdc in capacitors  203  by patching the circuit juncture  212  through to circuit juncture  214  at step  504  i.e. patching input B  226  to the output D  230  in  FIG. 2A  and disconnecting input A  224  to the output C  228  in  FIG. 2A . After step  504 , the circuit juncture  214  would provide a DC output of 35 Volts at circuit juncture  214  in  FIG. 2A  and this output would be channeled to the next stage for further processing at step  505 . 
     If Vdc (backup) is lesser than 35 Volts at step  507 , boosting would be performed by the DC voltage booster  202  to bring the Vdc to 35 Volts at step  509 . After boosting is done, the microcontroller  211  would, via control of one or more of the pins connected to points  251 ,  252 ,  253 ,  254 ,  255  and  266  in  FIG. 2A , release the voltage energy of Vdc in the capacitors  203  by patching the circuit juncture  212  through to circuit juncture  214  at step  504  i.e. patching input A  224  to the output C  228  in  FIG. 2A  and disconnecting input B  226  to the output D  230  in  FIG. 2A . After step  504 , the circuit juncture  214  would provide a DC output of 35 Volts at circuit juncture  214  in  FIG. 2A  and this output would be channeled to the next stage for further processing at step  505 . 
     Details on the DC boosting performed by the DC voltage booster  202  at step  509  would be provided as follows. 
       FIG. 2B  is an example of a circuit diagram of the DC voltage booster  202  in  FIG. 2A . The DC voltage booster  202  comprises a thyristor  231 , a resistor  232  and a capacitor  234 . It is appreciated that the resistor  232  could be made up of one or more variable or non-variable resistors. The thyristor  231  could be a silicon controlled rectifier thyristor or any other similar thyristor. The gate (corresponding with circuit juncture  217 ) of the thyristor  231  is connected to one end of capacitor  234 . In this case, the capacitor is charged whenever possible and when more than 12 Volts is received by the DC voltage booster  202  at the circuit juncture  222  after patching input A  224  to the output C  228 . The cathode (corresponding with circuit juncture  214 ) of the thyristor  231  is connected to the circuit juncture  214  and the anode (corresponding with circuit juncture  216 ) of the thyristor  231  is connected to output C  228 . The cathode (corresponding with circuit juncture  214 ) and the anode (corresponding with circuit juncture  216 ) of the thyristor  231  are coupled through the resistor  232 . 
     The microcontroller  211  is coupled to the DC voltage booster  202  at circuit junctures  214 ,  216  and  217 . More specifically, at circuit juncture  216 , 3 pins of the microcontroller  211 , namely ‘R’ for regulating, ‘C’ for comparator and ‘M’ for monitoring are connected to corresponding circuit points  241 ,  242  and  243  respectively. Circuit point  241  is in turn connected to output C  228  in  FIG. 2A  of the internal distribution point  221 . Circuit point  242  is connected to the resistor  232  and circuit point  243  is connected to the anode of the thyristor  231 . 
     At circuit juncture  214 , 3 pins of the microcontroller  211 , namely ‘R’ for regulating, ‘M’ for monitoring and ‘C’ for comparator are connected as follows. The ‘R’ and ‘M’ pins of the microcontroller  211  at circuit juncture  214  are connected to a circuit point  245  that is in turn connected to the cathode of the thyristor  231  and the terminal block  204 . The ‘C’ pin of the microcontroller  211  at circuit juncture  214  is connected to a circuit point  246  that is in turn connected to the resistor  232 . 
     At circuit juncture  217 , 4 pins of the microcontroller  211 , namely ‘M’ for monitoring, ‘REL’ for release, ‘H’ for hold and ‘R’ for regulating are all connected to one circuit point  244 . Circuit point  244  is connected to the capacitor  234  and the gate of the thyristor  231 . 
     In total, 10 pins of the microcontroller  211  are utilised at all 3 circuit junctures,  214 ,  216  and  217  and each pin is different from the other in this example. It is possible that one pin may be used at more than one circuit point by adjusting the algorithm run by the microcontroller  211 . 
     The ‘R’ pins are configured to help regulate the current flow and voltage at the various circuit points. ‘R’ pins may transmit regulating signals to activate the thyristor  231  for certain functions. 
     The ‘M’ pins are configured for monitoring the voltage and current values at the various circuit points. 
     The ‘C’ pins are configured for comparing voltage and/or current values or calculated resistance values based on the voltage and current values at the respective circuit points with predetermined threshold values. 
     The ‘H’ pin is configured to enable accumulation of charge at the gate (i.e. circuit juncture  217 ) of the thyristor  231 . The ‘H’ pin may transmit a hold signal, which in the present example could be a fixed 5 Volts signal, to work in conjunction with the regulating signal of the ‘R’ pin to activate the thyristor  231  in order of microseconds, e.g. including 0.001 to 2 microseconds to conduct current from the anode (circuit juncture  216 ) of the thyristor  231  to the gate (circuit juncture  217 ) of the thyristor  231  so that the voltage at the anode, V A , would become similar to the voltage at the gate, V G , of the thyristor  231  for a first time range. During the period of the hold signal, the voltage at the cathode, V C , of the thyristor  231  would remain low at about 2 Volts in the present example. 
     The ‘REL’ pin is configured to enable releasing of accumulated charge at the gate (i.e. circuit juncture  217 ) of the thyristor  231  when the thyristor  231  has been activated to conduct current from the gate (circuit juncture  217 ) to the cathode (circuit juncture  214 ). The ‘REL’ pin may transmit a release signal, which in the present example could be a fixed 2 Volts signal, to work in conjunction with the regulating signal of the ‘R’ pin to activate the thyristor  231  in order of microseconds, e.g. including 0.001 to 2 microseconds, to conduct current from the gate (circuit juncture  217 ) to the cathode (circuit juncture  214 ) so that the voltage at the gate, V G , would become similar to the voltage at the cathode, V C , of the thyristor  231  for a second time range. During the period of the release signal, the voltage at the cathode, V C , would rise up initially and follow the value of the voltage at the gate, V G , for a time period before falling. 
     From observation, the second time range where V G  is similar to V C  is longer than the first time range where V A  is similar to V G . The longer it is, the better is the voltage enhancement at the cathode of the thyristor  231 . 
     In addition, with regard to circuit juncture  216 , the ‘M’ pin (connected to point  243 ) is also configured as an output for current flow from input received at the ‘R’ pin (connected to point  241 ) by the microcontroller  211  or input received at the ‘C’ pin (connected to point  242 ) to the anode of the thyristor  231  by the microcontroller  211  at the appropriate time. Similarly, the ‘C’ pin connected to point  246  at the circuit juncture  214  is configured as an output for current flow from input received at the ‘R’ pin (connected to point  245 ) by the microcontroller  211  or input received at the ‘M’ pin (connected to point  245 ) to the resistor  232  by the microcontroller  211  at the appropriate time. With current flow being controlled in this case, resistance can be adjusted to affect voltage. Hence, the purpose of resistor  232  is to help to adjust, in this case to gain, resistance and in the process increase or maintain the desired voltage required. 
     For instance, the microcontroller  211  is configured to monitor the voltage at circuit juncture  214  using the ‘M’ pin connected to circuit point  245 . If the ‘C’ pin of microcontroller  211  to circuit point  246  detects that the voltage at circuit juncture  214  is lesser than or equal to 35 Volts, the microcontroller  211  could be configured to move on to monitor circuit juncture  222  in the manner described earlier with reference to  FIG. 2A . 
     With regard to the capacitor  234 , it is automatically charged whenever there is an excess of charge beyond a certain threshold at the gate of the thyristor  231 , for instance, whenever the voltage at the gate, V G , is greater than 12 Volts. 
     When the voltage of the DC input source  101  at circuit juncture  216  is detected by the ‘C’ pin of the microcontroller  211  to be lower than the desired voltage reference ( 213  in  FIG. 2A ) i.e. 35 Volts, but higher than 12 Volts, which is the lower limit of the possible fluctuation of the DC input source  101  (i.e. 12 to 45 Volts), the thyristor  231  would be set into forward conducting mode by a signal from the ‘R’ pin of the microcontroller  211  connected to circuit point  244  and current would be passed from its anode (corresponding with circuit juncture  216 ) to its cathode (corresponding with circuit juncture  214 ). 
     Voltage energy stored in the capacitor  234 , if sufficient, would be utilised to provide the boost to supplement the voltage at circuit juncture  214  to the desired voltage reference ( 213  in  FIG. 2A ) of 35 Volts when the voltage at circuit juncture  216  is detected by the ‘C’ pin of the microcontroller  211  to be lesser than 35 Volts. More details to obtain the preset desired voltage reference ( 213  in  FIG. 2A ) of, in this case, 35 Volts is provided as follows. 
       FIG. 6  shows a flowchart illustrating the steps taken to provide the DC boosting performed by the DC voltage booster  202 . In this instance, a DC output of 35 volt is to be obtained. Reference is made to the components in  FIGS. 2A and 2B . 
     At step  601 , the microcontroller  211  monitors the fluctuating DC input source  101  at circuit juncture  216  using the ‘M’ pin connected to circuit point  243 . 
     At step  602 , the ‘C’ pin of the microcontroller  211  checks if the Voltage of the DC input source  101 , Vdc, at circuit juncture  216  is greater than or equal to the lower limit of 12 Volts. 
     If Vdc is greater than or equal to 12 Volts at step  602 , the microcontroller  211  would at step  603  increase the current flow between the gate (circuit juncture  217 ) of the thyristor  231  and the cathode (circuit juncture  214 ) of the thyristor  231  by roughly 1%. 
     More specifically, in order of microseconds, e.g. including 0.001 to 2 microseconds, the microcontroller  211  would at step  603  send a first regulating signal through the ‘R’ pin connected to circuit point  244  to the gate (circuit juncture  217 ) of the thyristor  231  to activate the thyristor  231 . The ‘H’ pin sends the hold signal in conjunction with the ‘R’ pin at this first instance. Once the thyristor  231  is activated by the first regulating signal transmitted in conjunction with the hold signal of the ‘H’ pin, it is observed that the gate (circuit juncture  217 ) of the thyristor  231  and the anode (circuit juncture  216 ) of the thyristor  231  would begin to conduct and the voltage of the gate (circuit juncture  217 ) of the thyristor  231 , V G , would become similar to the voltage at the anode (circuit juncture  216 ) of the thyristor  231 , V A . The sending of the first regulating signal and hold signal is herein referred to as the holding step. It is “holding” in the sense that charge is accumulated or held at the gate of the thyristor  231 . 
     After a short period of transmitting the regulating and hold signals, the microcontroller  211  would send a second regulating signal through the ‘R’ pin connected to circuit point  244  to the gate (circuit juncture  217 ) of the thyristor  231  to activate the thyristor  231  to allow current to flow from the gate (circuit juncture  217 ) of the thyristor  231  to the cathode (circuit juncture  214 ) of the thyristor  231 . The ‘REL’ pin sends the release signal in conjunction with the ‘R’ pin at this second instance. Once the thyristor  231  is activated by the second regulating signal transmitted in conjunction with the release signal of the ‘REL’ pin, it is observed that the gate (circuit juncture  217 ) of the thyristor  231  and the cathode (circuit juncture  214 ) of the thyristor  231  would begin to conduct and the voltage of the gate (circuit juncture  217 ), V G , of the thyristor  231  would become similar to the voltage at the cathode (circuit juncture  214 ), V C , of the thyristor  231 . The sending of the second regulating signal and release signal is herein referred to as the releasing step. It is “releasing” in the sense that charge is accumulated at the gate of the thyristor  231  is being releases to the cathode of the thyristor  231 . 
     After the gate (circuit juncture  217 ) of the thyristor  231  and the cathode (circuit juncture  214 ) of the thyristor  231  begin to conduct, the microcontroller  211  sends a third regulating signal through the ‘R’ pin connected to circuit point  244  to the gate (circuit juncture  217 ) of the thyristor  231  in conjunction with the hold signal of the ‘H’ pin. It has been observed that in this third instance, the voltage at the gate, V G , begins to rise. Thereafter, the microcontroller  211  sends a fourth regulating signal through the ‘R’ pin connected to circuit point  244  to the gate (circuit juncture  217 ) of the thyristor  231  in conjunction with the release signal of the ‘REL’ pin. This causes the gate (circuit juncture  217 ) to conduct with the cathode (circuit  214 ) again and this time, the voltage at the cathode, V C , would have the risen value of V G . The rise in the V C  value at this instance accounts for the roughly 1% increase in current between circuit juncture  217  and circuit juncture  214 . 
     It is submitted that the use of the thyristor  231  in the manner aforementioned is unconventional and the results are obtained through observations. 
     If Vdc is lesser than 12 Volts at step  602 , nothing is done and the process ends at step  609 . 12 Volts is the minimal voltage which the DC input source  101 , in this case a solar panel supplying 12-45 Volts, would provide. An undesirable fall in voltage at the circuit juncture  214  would occur when Vdc is lesser than 12 Volts. However, it is expected that such occurrence would be rare in normal operation as 12 Volts is the minimum voltage that the DC input source  101  provides. 
     After step  603 , the microcontroller  211  checks again at step  604  and at circuit juncture  216  to see if the Voltage of the DC input source  101 , Vdc, is greater than or equal to the lower limit of 12 Volts using the respective ‘C’ pin. 
     If Vdc is greater than or equal to 12 Volts at step  604 , the microcontroller  211  would check at step  605  whether a resistance value, R, remains constant from a previous calculation of the R value. The microcontroller  211  makes use of the ‘C’ pin connected to circuit point  246  to perform the check at step  605 . R is calculated from the voltage (V G ) and current values at the cathode of the thyristor i.e. at circuit juncture  214 , which can be acquired by the microcontroller  211  through the respective ‘M’ pin connected to circuit point  245 . 
     If Vdc is lesser than 12 Volts at step  604 , the microcontroller  211  would draw voltage energy from the capacitor  234 , if sufficient, at step  610 . If there is sufficient charge, the voltage energy can be drawn by the microcontroller  211  activating the thyristor  231  to allow current to flow from the gate of the thyristor  231  at circuit juncture  217  to the cathode of the thyristor  231  at circuit juncture  214 . Similarly, such activation can be done with the appropriate regulating signal through the respective ‘R’ pin use in conjunction with the release signal through the ‘REL’ pin. After step  610 , step  602  is performed again. 
     If the resistance value, R, remains constant at step  605 , the microcontroller  211  will check through the ‘C’ pin connected to point  246  whether the current at the cathode (circuit juncture  214 ) of the thyristor  231  has reached a predetermined current value required to provide sufficient power for a predefined maximum loading condition of the present DC to AC power conversion system ( 100  in  FIG. 1 ). If not, the current would be increased by repeating the holding step followed by the releasing step one or more times to reach the predetermined current value. Otherwise, the next process to be carried out by the DC to AC conversion subsystem ( 300  in  FIG. 1 ) would begin. 
     If the resistance value, R, is not constant at step  605 , the microcontroller  211  would at circuit juncture  214  channel the current received by the ‘R’ and ‘M’ pins connected to point  245  to output through the ‘C’ pin connected to point  246  at step  608 . What follows after channeling of the current is a repeat of the holding step to accumulate more charge at the gate (circuit juncture  217 ) of the thyristor  231 . This time, the duration of the regulating and hold signal is a few microseconds longer so as to build up the charge at the gate (circuit juncture  217 ) of the thyristor  231  until it reaches a maximum holding point, which is just before the voltage at the gate, V G , reaches the breaking voltage of the thyristor  231  that can break down the thyristor  231 . After reaching the maximum holding point, the releasing step is carried out to release the accumulated charge from the gate (circuit juncture  217 ) of the thyristor  231  to the cathode (circuit juncture  214 ) of the thyristor  231 . After the releasing step, step  605  is performed again to check whether R is constant with the previous R value that was read. 
       FIG. 9  illustrates an example of DC Voltage boosting conducted at the DC voltage booster  202 . In particular, the holding step occurring in a first instance and the releasing step occurring in a second instance are illustrated. The results are obtained from observations. It is noted that although specific timings in order of microseconds, e.g. including 0.001 to 2 microseconds, are provided, they are to be regarded as estimates only and they pertain to one commercially available standard Silicon-Controlled Rectifier (SCR) thyristor. The timings may change depending on the constitution and design of the thyristor being used. It is possible to have timings longer or shorter to an extent that voltage at the cathode of the thyristor is enhanced as desired. 
     With reference to  FIG. 2B , it is assumed in  FIG. 9  that the reading at the voltage of the anode (circuit juncture  216 ) of the thyristor  231 , V A , is 12 Volts. The aim is to boost the voltage at the cathode (circuit juncture  217 ) of the thyristor  231 , V C , to achieve a relatively stable 35 Volts (DC) with the 12 Volts at V A . For convenience, in parts of the text as follows, it is understood that the corresponding hold signal or release signal would accompany the regulating signal according to the mention of the holding step and the releasing step described earlier. 
     At the beginning, the microcontroller  211  sends a regulating signal for a first time period  902  of about 0.167 microseconds. Within the period  902 , the regulating signal begins with a pulsating wave  903 , firstly at 2 Volts for about 0.0278 microseconds followed by 5 volts for another about 0.0278 microseconds. Thereafter, the regulating signal slopes linearly to 12 Volts for about 0.0556 microseconds in a second time period and plateaus at 12 Volts [i.e. voltage of the anode (circuit juncture  216 ) of the thyristor  231 , V A ] for another about 0.0556 microseconds. The pulsating wave  903  of the period  902  is responsible for activating the thyristor  231  to conduct from the anode (circuit juncture  216 ) to the gate (circuit juncture  217 ). It is appreciated that the pulsating wave  903  may comprise one or more pulses. The pulsating wave  903  may also be regarded as a spike and need not necessarily be square shaped as shown in  FIG. 9 . During activation, the voltage at the gate (circuit juncture  217 ), V G , slopes linearly to about 12 Volts at point  913  in  FIG. 9  to the voltage value at the anode (circuit juncture  216 ) in about 0.0833 microseconds. Once activated, V G  would maintain at 12 Volts until about 1.08 microseconds later where there is a 1% current increase point  914  where V G  also correspondingly increases by 1%. During the period  902 , charge is accumulated at the gate (circuit juncture  217 ), thereby performing the holding step. 
     After the period  902 , the regulating signal undergoes a period  904  of about 0.5833 microseconds, which performs the releasing step, where the thyristor  231  is activated to conduct from the gate (circuit juncture  217 ) to the cathode (circuit juncture  214 ). The waveform of the releasing step in period  904  firstly falls generally linearly from 12 Volts to 2 Volts for about 0.0833 microseconds in a third time period but at about midway, there is present a sharp fall  905  (i.e. a fourth time period) lasting about 0.0167 microseconds. Thereafter, the waveform remains at 2 Volts until about 0.5 microseconds later. The effect of period  904  is that the thyristor  231  releases all the charge accumulated at the gate (circuit juncture  217 ) during the period  902  to the cathode (circuit juncture  214 ). This causes the voltage at the cathode (circuit juncture  214 ), V C , to slope linearly to about 12 Volts at point  914  in  FIG. 9 . The voltage at the cathode (circuit juncture  214 ), V C , plateaus at about 12 Volts until the charge released begins to run out, thereby causing V C  to fall from 12 Volts to 2 Volts towards the end of the period  904 . 
     After the period  904 , the regulating signal undergoes another period  906  of about 0.25 microseconds, which performs the holding step. The period  906  begins with a sharp spike  907  of about 5 Volts that lasts about the same time as the sharp dip  905 . After the spike  907 , the waveform rises linearly from about 2 Volts to 12 Volts and remains for about 0.0556 microseconds at 12 Volts before reaching a point where it is observed that there is a slight rise in voltage beyond 12 Volts. The slight rise continues on for about 0.111 microseconds. This slight rise would be responsible for about 1% increase in current and voltage at V C  in the period  908  discussed later. The effect of period  906  is that it activates the thyristor  231  to accumulate and hold charge at the gate (circuit juncture  217 ). V C  remains at 2 Volts during the duration of period  906  as no charge is released to the cathode (circuit juncture  214 ). 
     After the period  906 , the regulating signal undergoes another period  908  of about 0.4165 microseconds, which performs the releasing step, where the thyristor  231  is activated to conduct from the gate (circuit juncture  217 ) to the cathode (circuit juncture  214 ). The waveform of the releasing step in period  908  firstly falls generally linearly from 12 Volts to 2 Volts for about 0.0833 microseconds but at about midway, there is present a sharp fall  905  lasting about 0.0167 microseconds. Thereafter, the waveform remains at 2 Volts for about 0.278 microseconds followed by the same sharp spike  907  and a linear slope rising from 2 Volts to 35 Volts in about 0.0833 microseconds. The sudden increase to 35 Volts is a notable observation. The effect of period  908  is that the thyristor  231  releases all the charge accumulated at the gate (circuit juncture  217 ) during the period  906  to the cathode (circuit juncture  214 ). This causes the voltage at the cathode (circuit juncture  214 ), V C , to slope linearly to about 12 Volts at point  912  in  FIG. 9 . There is a 1% increase in the current and voltage because of the slight rise beyond 12 Volts during the period  906 . The voltage at the cathode (circuit juncture  214 ), V C , plateaus at about 12 Volts until the charge released begins to run out, thereby causing V C  to fall from 12 Volts to 2 Volts towards the end of the period  908 . 
     After the period  908 , the regulating signal undergoes another period  910  of about 0.15 microseconds, which performs the holding step. Basically, the regulating signal is held at 35 Volts during the period  910 . During period  910 , V C  remains at 2 Volts. 
     After the holding step in period  910 , the releasing step is performed again. In this instance, the regulating signal falls generally linearly from 35 Volts to 2 Volts for about 0.0833 microseconds but at about midway, there is present a sharp fall  905  lasting about 0.0167 microseconds. The effect of the releasing step at this instance is quite significant in that V C  begins to rise from 2 Volts to 35 Volts at point  915  in  FIG. 9 . Thereafter, V C  plateaus at about 35 Volts until the charge released begins to run out, thereby causing V C  to fall from 35 Volts to 2 Volts. 
     The period  911  between the 1.25 microseconds mark and the 1.75 microseconds mark in  FIG. 9  is then repeated to continue to cause V C  to plateau at about 35 Volts, thereby maintaining a relatively stable DC Voltage output of about 35 Volts. It is submitted that within the order of microseconds, the releasing time i.e. the time where V C  is kept at 35 Volts is about 6 times longer than the holding time i.e. the time V C  is at 2 Volts, thus a high efficiency is obtained in the Voltage boosting. 
     It is appreciated that there are times where period  906  is required to be repeated before the significant boost of V C  is achieved after period  910  can occur. 
     With regard to V G , after the 1% increase at the time instance of point  914  in  FIG. 9 , the 1% increase will sustain until the 1.25 microsecond mark, thereafter voltage increases about linearly to 35 Volts at about the time when period  910  begins. Thereafter, V G  remains at about 35 Volts. 
       FIG. 3A  is a circuit diagram of the DC to AC conversion subsystem  301  in  FIG. 1 . The DC to AC converter  301  comprises eight Insulated gate Bipolar Transistors (“IGBTs”)  321 ,  322 ,  323 ,  324 ,  325 ,  326 ,  327  and  328 . All the IGBTs described herein are of the same design. The cathodes of IGBT  321  and IGBT  323  are connected to the positive terminal  223  of the boosted DC voltage obtained from the DC to DC conversion subsystem  200 . The positive terminal  223  at the terminal block  204  is also coupled to one end of a capacitor  331  and to a Pulse Width Modulation Firing and Loss compensation circuit  311 . The other end of the capacitor  331  is connected to ground. It is noted that the words firing and triggering in relation to IGBTs are used interchangeably. 
     It is appreciated that the IGBTs as herein described may be replaced with filtering circuits in other examples. 
     The emitter ends of IGBT  321  and IGBT  323  are connected to two different ends of a primary winding  341  of a transformer  340 . The emitter ends of IGBT  321  and IGBT  323  are also coupled to the cathodes of IGBT  322  and IGBT  324 , respectively. The emitter ends of IGBT  322  and IGBT  324  are in turn connected to ground. 
     Similarly, the emitter ends of IGBT  325  and IGBT  327  are connected to two different ends of a secondary winding  342  of the transformer  340 . The emitter ends of IGBT  325  and IGBT  327  are also coupled to the cathodes of IGBT  326  and IGBT  328 , respectively. The emitter ends of IGBT  326  and IGBT  328  are in turn connected to ground. 
     Each of the gates of the IGBT  321 ,  322 ,  323 ,  324 ,  325 ,  326 ,  327  and  328  is coupled to the Pulse Width Modulation Firing and Loss compensation circuit  311 . The Pulse Width Modulation Firing and Loss compensation circuit  311  provides the respective IGBT&#39;s triggering voltage, pulse timing and sequence for performing Pulse Wave Modulation (PWM). By measuring the voltages at the secondary winding  342  of the transformer  340  and by running an algorithm that determines modulation values of the output signal of the transformer  340  at the secondary winding  342  and/or and compares the modulation values against predefined desirable reference modulation values, the microcontroller  311  would adjust the triggering sequence to create an AC voltage waveform with the desired frequency (i.e.  230 - 240  Alternating Voltage Supply) at the output of the transformer  340  at the secondary winding  342 . The microcontroller  311  also compares the voltages measured with predefined reference voltage values and relies on the comparison to adjust the triggering of the IGBTs. Modulation values refer to peak to peak voltage values of a voltage signal. In this case, the triggering or firing sequence of the IGBTs  321 ,  322 ,  323 ,  324 ,  325 ,  326 ,  327  and  328  are looped continuously in order i.e.  321 , followed by  322 , followed by  323 , followed by  324 , followed by  325 , followed by  326 , followed by  327 , followed by  328 , back to  321  and so on. 
     There are losses after every firing of each of the eight IGBTs  321 ,  322 ,  323 ,  324 ,  325 ,  326 ,  327  and  328 . The Pulse Width Modulation Firing and Loss compensation  311  helps to reduce those losses by monitoring every firing and providing the required compensation to ensure that the DC to AC conversion process is efficient. 
       FIG. 3B  is a circuit diagram of the Pulse Width Modulation (PWM) Firing and Loss compensation circuit  311  in  FIG. 3A . 
     The PWM Firing and Loss compensation circuit  311  comprises two integrated circuits IC 1   370  and IC 2   380 . Each of IC 1   370  and IC 2   380  has eight pins. IC 1   370  and IC 2   380  are connected to the microcontroller  211  via pins  371  and  381  respectively. IC 1   370  and IC 2   380  receive commands via pins  371  and  381  respectively from the microcontroller  211  to carry energy compensation and to control the firing of the eight IGBTs  321 ,  322 ,  323 ,  324 ,  325 ,  326 ,  327  and  328 . Apparently, firing of the IGBTs  321 ,  322 ,  323 ,  324 ,  325 ,  326 ,  327  and  328  takes place in conjunction with the compensation of energy losses due to the firing. 
     Power is supplied to both IC 1   370  and IC 2   380  via pins  372  and  382  respectively from the positive terminal  223 , which has a boosted DC output from the DC Voltage booster  202 . Some circuitries (not shown in  FIG. 3B ) may be connected to the positive terminal  223  and the microcontroller  211  to ensure that IC 1   370  and IC 2   380  receive the desired power supply required to operate. 
     The emitter ends of the IGBTs  321  and  322 , which are connected to each other, are monitored by pin  377  of IC 1   370 . IC 1   370  monitors the resistance values calculated at the emitter ends of the IGBTs  321  and  322  as well as the current values. Similarly, the emitter ends of the IGBTs  323  and  324 , which are connected to each other, are monitored by pin  378  of IC 1   370 . IC 1   370  monitors the resistance values calculated at the emitter ends of the IGBTs  321 ,  322 ,  323  and  324  as well as the current values at those emitter ends. The monitored current and resistance values are saved into a memory of the microcontroller  211  or the IC 1   370 , where necessary, for comparison with predefined desired reference resistance and current values. Whenever there is a difference between the desired reference resistance and current values and the actual resistance and current values monitored by pins  377  or  378 , the microcontroller  211  would send commands to instruct IC 1   370  to make compensation or, alternatively, IC 1   370  is configured to automatically carry out the necessary compensation. The memory may be Read Only Memory (ROM), Random Access Memory (RAM), flash memory, a magnetic disk and the like. 
     A pin  373  of the IC 1   370  is connected to a circuit loop  352  comprising a resistor R 1   361 , a second resistor R 2   369  and a variable resistor VR 1   362 . R 2   369  is connected in series with VR 1   362  and R 1   361  is connected in parallel with R 2   369  and VR 1   362 . The variable resistor VR 1   362  is adjustable by the microcontroller  211  to compensate for any difference between the calculated resistance value monitored at pin  377  or  378  and a predefined desired reference resistance value made available to the microcontroller  211  or IC 1   370  for comparison. 
     A pin  374  of the IC 1   370  is connected to one end of a capacitor C 1   363 , which is controlled by IC 1   370  during operation. The same end of C 1   363  is also connected to the positive terminal  223 . The other end of C 1   363  is connected to ground. C 1   363  is used to provide charge to compensate current when the current value detected by pin  373  is lower than a predefined desired reference current value made available to the microcontroller  211  or IC 1   370  for comparison. C 1   363  is charged whenever possible by the boosted DC voltage at the positive terminal  223 . 
     A pin  375  of the IC 1   370  is connected to a resistor R 3   356 . A base end of an NPN transistor TR 1   364  is connected in series with the resistor R 3   356 . A emitter end of the transistor TR 1   364  is connected to ground and A collector end of the transistor TR 1   364  is connected to the gates of the IGBTs  321 ,  322 ,  325  and  326 . A resistor R 4   355  is in turn connected at one end to the gates of the IGBTs  321 ,  322 ,  325  and  326  and at another end to the positive terminal  223 . 
     The resistor R 3   356  is used to further refine the resistance value monitored by pin  377  that is compared with the predefined desired reference resistance value made available to the microcontroller  211 . The further refinement provided by R 5   356  compensates for energy losses incurred by circuit loop  352  and by capacitor  363  when they are utilised to compensate for energy losses due to firing of IGBTs  321  and  322 . 
     A pin  376  of the IC 1   370  is connected to a resistor R 5   366 . A base end of an NPN transistor TR 2   365  is connected in series with the resistor R 5   366 . An emitter end of the transistor TR 1   364  is connected to ground and a collector end of the transistor TR 1   364  is connected to the gates of the IGBTs  323 ,  324 ,  327  and  328 . A resistor R 6   354  is in turn connected at one end to the gates of the IGBTs  323 ,  324 ,  327  and  328  and at another end to the positive terminal  223 . 
     The resistor R 5   366  is used to further refine the resistance value monitored by pin  378  that is compared with the predefined desired reference resistance value made available to the microcontroller  211 . The further refinement provided by R 5   366  compensates for energy losses incurred by circuit loop  352  and by capacitor  363  when they are utilised to compensate for energy losses due to firing of IGBTs  323  and  324 . 
     Both transistors TR 1   364  and TR 2   365  are used for overcurrent protection at their respective points in the circuit, in particular, for protecting against overcurrent caused by the boosted DC Voltage at the positive terminal  223 . 
     A pin  388  of the IC 2   380  is connected to the output of the secondary windings  342 . Pin  388  is used for monitoring the voltage values calculated at the output of the secondary windings  342 . The monitored voltage values are saved into a memory of the microcontroller  211  or the IC 2   380 , where necessary, for comparison with predefined desired reference voltage values. Whenever there is a difference between the desired reference voltage values and the actual voltage values monitored at the output of the secondary windings  342 , the microcontroller  211  would send commands to instruct IC 2   380  to make compensation or, alternatively, IC 2   380  is configured to automatically carry out the necessary compensation. The memory may be Read Only Memory (ROM), Random Access Memory (RAM), flash memory, a magnetic disk and the like. 
     A pin  383  of the IC 2   380  is connected to one end of a capacitor C 3   358 , which is controlled by IC 1   380  during operation. The same end of C 3   358  is also connected to the positive terminal  223 . The other end of C 3   358  is connected to ground. C 3   358  is used to provide charge to compensate current when the voltage value detected by pin  388  is lower than a predefined desired reference voltage value made available to the microcontroller  211  or IC 2   380  for comparison. C 3   358  is charged whenever possible by the boosted DC voltage at the positive terminal  223 . 
     Similarly, a pin  384  of the IC 2   380  is connected to one end of a capacitor C 2   353 , which is controlled by IC 1   380  during operation. The same end of C 2   353  is also connected to the positive terminal  223 . The other end of C 2   353  is connected to ground. C 2   353  is used to provide charge to compensate current when the voltage value detected by pin  388  is lower than the predefined desired reference voltage value made available to the microcontroller  211  or IC 2   380  for comparison. C 2   353  is charged whenever possible by the boosted DC voltage at the positive terminal  223 . 
     IC 2   380  comprises another pin  385  that is connected to one end of a resistor R 4   355 . The other end of R 4   355  is connected to the gates of IGBTs  321 ,  322 ,  325  and  326 . R 4   355  compensates for losses due to firing of IGBTs  325  and  324  based on differences between voltage values detected by pin  388  and the predefined desired reference voltage value made available to the microcontroller  211  or IC 2   380  for comparison. 
     Similarly, IC 2   380  comprises a further pin  386  that is connected to one end of a resistor R 6   354 . The other end of R 6   354  is connected to the gates of IGBTs  323 ,  324 ,  327  and  328 . R 6   354  compensates for losses due to firing of IGBTs  327  and  328  based on differences between voltage values detected by pin  388  and the predefined desired reference voltage value made available to the microcontroller  211  or IC 2   380  for comparison. 
     In the present example, C 2   353 , C 3   358 , R 4   355  and R 6   354  are connected in parallel to one another. Furthermore, a pin  387  of IC 2   380  is connected to ground to provide for any grounding needs required by IC 2   380 . 
     Details of the method steps applied by the microcontroller  211 , IC 1   370  and/or IC 2   380  are described as follows with reference to  FIG. 7 . Reference is made to components in  FIGS. 3A and 3B . 
     In the present example, the DC voltage signal, 35 Volts, received from the positive terminal  223  of the terminal block  204  changes into an AC signal after the fourth IGBT i.e.  324  is triggered. The operation process for triggering or firing the eight IGBTs  321 ,  322 ,  323 ,  324 ,  325 ,  326 ,  327  and  328  loops until a condition is satisfied. The condition is that a Vout value indicative of the output signal obtained at the secondary winding  342  of the transformer  340  becomes equal to a Vref value that is a predefined desirable reference voltage value (also known as the initial look-up voltage value) made available to the microcontroller  211  for comparison with Vout. Vout is a value that would be changing according to the triggering of the IGBTs. Vref is selected based on the desired AC output requirements of the DC to AC power enhancer system  100  in  FIG. 1 , for example, Vref could be 110-120 or 230-240 Volts (root mean square) (i.e. Vrms). 
     At step  701 , the microcontroller  211  reads or retrieves the initial look-up voltage value, Vref from a memory. The memory may reside in the microcontroller  211 , the IC 1   370  or IC 2   380  or externally connected to the microcontroller  211 , the IC 1   370  or IC 2   380 . The memory may be Read Only Memory (ROM), Random Access Memory (RAM), flash memory, a magnetic disk and the like. 
     After step  701 , the microcontroller  211  checks the Pulse Width Modulation (PWM) control signal at the secondary winding  342  at step  702 . The step of checking the PWM control signal is for determining the Vout value, which is a Voltage reading extracted at a specific time instance of the PWM control signal. The PWM control signal is detected via pin  388  of IC 1   380 . Vout is a value that may vary according to the triggering of the IGBTs. 
     After step  702 , the Vout value is obtained from the PWM control signal and inputted to the microcontroller  211  via IC 2   380  at step  703 . 
     Upon receiving the value of Vout at step  703 , the microcontroller  211  compares the value of Vout with the predefined desirable reference voltage value, Vref, at step  704 . 
     Step  705  performs the comparison carried out by the microcontroller  211  at step  704 . The microcontroller  311  checks at step  705  whether Vout is equaled to Vref. 
     If Vout equals to Vref at step  705 , the microcontroller  211  determines an M value i.e. a modulation value for the value of Vout at step  706 . The M value refers to the peak to peak values of the PWM control signal. For example, if Vout is initially 35 Volts (DC) before the firing of the IGBTs, the modulation value of the Vout value is also 35 Volts, which is the peak to peak voltage of the 35 Volts (DC). After firing the IGBTs and acquiring an AC voltage signal, the M value changes according to the peak to peak voltage of the AC voltage signal acquired. In this example, ultimately, the desirable output AC voltage signal to be acquired is a sinusoidal signal having a root mean square voltage, Vrms, of 230-240 or 110-120. It is appreciated that Vrms equals to Vpeak divided by square root of 2, where Vpeak is half of the peak to peak voltage of the AC voltage signal. 
     If Vout is not equaled to Vref at step  705 , the microcontroller  211  would at step  710  trigger all the eight IGBTs  321 ,  322 ,  323 ,  324 ,  325 ,  326 ,  327  and  328  in that sequence, followed by proceeding to step  702  again. Steps  702 ,  703 ,  704  and  705  would loop until the triggering of the eight IGBTs have caused Vout to be equaled to Vref. It is appreciated that the microcontroller  211  may trigger one or more of the eight IGBTs in any sequence if it is preferred to ensure that Vout equals to Vref. 
     After step  706 , the microcontroller  211  reads or retrieves a look-up modulation value from a memory at step  707 . The look-up modulation value is a predefined desirable reference modulation value made available to the microcontroller  211  for comparison with the M value determined at step  706 . The look-up modulation value is selected based on the desired AC output requirements of the DC to AC power enhancer system  100  in  FIG. 1 . The memory may reside in the microcontroller  211 , the IC 1   370  or IC 2   380  or externally connected to the microcontroller  211 , the IC 1   370  or IC 2   380 . The memory may be Read Only Memory (ROM), Random Access Memory (RAM), flash memory, a magnetic disk and the like. 
     After reading or retrieving the look-up modulation value at step  707 , the microcontroller  311  checks whether the M value determined at step  706  equals to the look-up modulation value at step  708 . 
     If during step  708 , the M value determined at step  706  equals to the look-up modulation value read at step  707 , this would mean that the M value (i.e. peak to peak voltage value) of the output AC waveform at the secondary windings  342  of the DC to AC converter  301  has fulfilled the desired modulation value requirements. As such, nothing further needs to be done and the process ends at step  709 . The next process i.e. AC power boosting carried out by the AC power booster  401  in  FIG. 1  may then commence. 
     However, if during step  708 , the M value determined at step  706  is not equaled to the look-up modulation value read at step  707 , the microcontroller  211  would at step  710  trigger all the eight IGBTs  321 ,  322 ,  323 ,  324 ,  325 ,  326 ,  327  and  328  in that sequence, followed by proceeding to step  702  again. Steps  702  onwards until  708  would loop till the triggering of the IGBT(s) have caused the M value determined at step  706  to be equaled to the look-up modulation value read at step  707 . 
     Steps  706  to  708  are additional steps included to ensure that the desired AC output requirements could be obtained at the second winding  342  of the transformer  340 . The desired AC output requirements could already be obtained through steps  702  to  705 . 
     It is appreciated that for the stage of DC to AC conversion, depending upon the power capacity of the circuit i.e. how much power the circuit is to provide, lesser number of IGBTs may be used. It is appreciated that the number of IGBTs that could be used may range between 2 to 8. 
       FIGS. 11 and 12  together illustrate possible PWM control signals (voltage vs time format) obtained after the firing of each of the eight IGBTs  321 ,  322 ,  323 ,  324 ,  325 ,  326 ,  327  and  328  in that sequence. In the case of the firing results in  FIGS. 11 and 12 , the PWM control signal of IGBT  328  is the desired AC output. In  FIG. 11 , the PWM control signals obtained by the first four IGBTs  321 ,  322 ,  323  and  324  are still DC signals. In  FIG. 12 , the PWM control signals obtained by the last four IGBTs  325 ,  326 ,  327  and  328  after the firing of the first four IGBTs  321 ,  322 ,  323  and  324  are AC signals. 
       FIG. 4  shows a circuit diagram of the AC power booster  401  in  FIG. 1 . The AC power booster  401  comprises two thyristors  431  and  432 , two resistors  422  and  423 , a diode  424  and a connected load  420 . It is appreciated that the resistors  422  and  423  could be made up of one or more variable or non-variable resistors. The thyristor  431  could be a silicon controlled rectifier thyristor or any other similar thyristor. There are various circuit junctures  411 ,  434 ,  436  and  438  having connections to the microcontroller  211  described with reference to previous Figures. The gate of the thyristor  431  is connected to the circuit juncture  438 . The anode of the thyristor  431  is connected to the circuit juncture  411 . The cathode of the thyristor  431  is connected to the circuit juncture  434 . One end B 0   410  of the secondary winding  342  of the transformer  340  in  FIG. 3A  is connected to the circuit juncture  411  and the other end B 1   412  of the secondary winding  342  of the transformer  340  is connected to the circuit juncture  436 . Circuit juncture  434  is connected to circuit juncture  436 . The resistor  423  is connected in series with the diode  424 . The diode anode of the diode  424  is connected to the resistor  423  and the diode cathode of the diode  424  is connected to circuit juncture  438 . The resistor  422  is connected between circuit junctures  411  and  436 . The anode of the thyristor  432  is connected to the circuit juncture  434  and the gate and cathode of the thyristor  432  are each connected to the load  420  to drive the load  420  with the AC signal enhanced by the AC power booster  401 . Voltage at the cathode of the thyristor  431  is enhanced. Current is led to the anode of the thyristor  432  from the cathode of the thyristor  431  to apply the enhanced voltage to the anode of the thyristor  432 . 
     At circuit juncture  411 , 3 pins of the microcontroller  211 , namely ‘R’ for regulating, ‘C’ for comparator and ‘M’ for monitoring are connected to corresponding circuit points  413 ,  414  and  415  respectively. Circuit point  413  is in turn connected to B 0   410 . Circuit point  414  is connected to the resistor  422  and circuit point  415  is connected to the anode of the thyristor  431 . 
     At circuit juncture  411 , the ‘R’ pin connected to circuit point  413  helps to regulate current flow between circuit points  413 ,  414  and  415 . That is, it helps to conduct current flow between circuit points  413  and  414  through the microcontroller  211 , and current flow between circuit points  413  and  415  through the microcontroller  211  when necessary. The ‘C’ pin connected to circuit point  414  enables comparison between the Resistance value [at circuit point  415  and the voltage value monitored by the ‘M’ pin connected to point  416 . If the voltage value at point  415  is lesser than the voltage value at point  416 , current flow between circuit points  413  and  414  would occur. Otherwise, current flow between circuit points  413  and  415  would carry out. The ‘M’ pin connected to circuit point  415  monitors the voltage value of point  415  and stores it in a cache memory of the microcontroller  211  for comparison by the ‘C’ pin. 
     At circuit juncture  436 , 3 pins of the microcontroller  211 , namely for regulating, ‘C’ for comparator and ‘M’ for monitoring are connected to corresponding circuit points  403 ,  402  and  404  respectively. Circuit point  403  is in turn connected to B 1   412 . Circuit point  402  is connected to the resistor  422  and circuit point  404  is connected to the resistor  423 . 
     At circuit juncture  436 , the ‘C’ pin connected to point  402  enables comparison between a first resistance value calculated based on current and voltage at point  402  and a first predefined resistance value. The ‘R’ pin connected to point  403  is enabled to allow current to flow from the point  402  to point  404  through the microcontroller  211  if the first resistance value is lesser than the first predefined resistance value. Otherwise, the ‘R’ pin connected to point  403  is enabled to allow current to flow between the points  403  and  402  through the microcontroller  211 . The ‘M’ pin  404  outputs current associated with the first resistance value calculated at point  402  if the first resistance value is lesser than the first predefined resistance value. It is appreciated that the first predefined resistance value is selected accordingly to contribute towards voltage enhancement at the cathode of thyristor  431 . 
     At circuit juncture  434 , 3 pins of the microcontroller  211 , namely ‘R’ for regulating, ‘C’ for comparator and ‘M’ for monitoring are connected as follows. The ‘R’ and ‘M’ pins are connected to circuit point  416 . The ‘C’ pin is connected to circuit point  417 . Circuit point  416  is in turn connected to the cathode of the thyristor  431 . Circuit point  417  is connected to a circuit point  418 . Circuit point  418  is in turn connected to circuit point  403  and B 1   412 . 
     At circuit point  434 , the ‘C’ pin connected to point  417  reacts based on a comparison between a second resistance value calculated based on current and voltage monitored at point  416  (by the ‘M’ pin connected to point  416 ) and a second predefined resistance value. Current always flow between the cathode of the thyristor  431  and the anode of the thyristor  432 . However, if the second resistance value calculated is lesser than the second predefined resistance value, the ‘R’ pin connected to point  416  is enabled to allow current to flow between the points  416  and  417  through the microcontroller  211 . The ‘M’ pin connected to point  416  monitors the current and voltage at point  416  and saves their values in a memory for the calculation of the second resistance value. It is appreciated that the second predefined resistance value is selected accordingly to contribute towards voltage enhancement at the cathode of the thyristor  431 . 
     Circuit points  418  and  403  are connected to 2 pins, namely a ‘M’ (Monitoring) pin and an ‘R’ (Regulating) pin respectively, of the microcontroller  211 . 
     The ‘M’ pin connected to point  418  monitors the current and voltage at point  418  for calculation of a third resistance value at point  418 . The ‘R’ pin connected to points  403  and  418  enables current flow between points  403  and  418  when the third resistance value is greater than a third predefined resistance value. It is appreciated that the third predefined resistance value is selected accordingly to contribute towards voltage enhancement at the cathode of the thyristor  431 . 
     Each of the first, second and third predefined resistance values may vary depending on the power capacity of AC power booster  401  and range from 1 to 100 ohms. For example, for the AC power booster  401  to provide a power supply capacity of 1200 Watts, each of the first, second, and third predefined resistance values may be about 10 ohms. 
     At circuit juncture  438 , 4 pins of the microcontroller  211 , namely ‘M’ for monitoring, ‘REL’ for release, ‘H’ for hold and ‘R’ for regulating are all connected to one circuit point  405 . Circuit point  405  is connected to the diode cathode end of the diode  424  and the gate of the thyristor  431 . 
     At circuit juncture  438 , the ‘R’ pin connected to point  405  is configured to transmit regulating signals to activate the thyristor  431  for current flow between its anode and cathode and between its gate and cathode. 
     The ‘M’ pin connected to point  405  is configured for monitoring the voltage and current values at circuit point  405 . 
     The ‘H’ pin connected to point  405  is configured to enable accumulation of charge at the gate (i.e. circuit juncture  438 ) of the thyristor  431 . The ‘H’ pin connected to point  405  may transmit a hold signal, which in the present example could be a fixed 5 Volts signal, to work in conjunction with the regulating signal of the ‘R’ pin connected to point  405  to activate the thyristor  431  in order of microseconds, e.g. including 0.001 to 2 microseconds, to conduct current from the anode of the thyristor  431  to the gate so that a resistance value calculated based on current and voltage monitored at the anode, R A , would become similar to a resistance value calculated based on current and voltage monitored at the gate, R G , of the thyristor  431  for a first time range. During the period of the hold signal, the voltage at the cathode, V C , of thyristor  431  would not be enhanced. 
     The ‘REL’ pin is configured to enable releasing of accumulated charge at the gate of the thyristor  431  when the thyristor  431  has been activated to conduct current from the gate of the thyristor  431  to the cathode of the thyristor  431 . The ‘REL’ pin may transmit a release signal, which in the present example could be a fixed 2 Volts signal, to work in conjunction with the regulating signal of the ‘R’ pin to activate the thyristor  431  in order of microseconds, e.g. including 0.001 to 2 microseconds, to conduct current from the gate of the thyristor  431  to the cathode of the thyristor  431  so that the resistance value calculated based on current and voltage monitored at the gate, R G , would become similar to the resistance value calculated based on current and voltage monitored at the cathode, R C , of the thyristor  431  for a second time range. During the period of the release signal, R C  would rise up initially and follow the value of R G  for a while before falling. During the period of the release signal, the voltage at the cathode, V C , would be enhanced to provide sufficient power output or drive to support the load  420 . 
     From observation, the second time range where R G  is similar to R C  is longer than the first time range where R A  is similar to R G . The longer it is, the better is the voltage enhancement at the cathode of the thyristor  431 . 
     In total, 15 pins of the microcontroller  211  are utilised at all 4 circuit junctures,  411 ,  434 ,  436  and  438  and each pin is different from the other in this example. It is possible that one pin may be used at more than one circuit point by adjusting the algorithm run by the microcontroller  211 . 
     With regard to circuit juncture  411 , the ‘M’ pin (connected to point  415 ) is configured for outputting signal from the ‘R’ pin (connected to point  413 ) or the ‘C’ pin (connected to point  414 ) to the anode of the thyristor  431  at the appropriate time. Similarly, the ‘M’ pin connected to point  403  at the circuit juncture  436  is configured for outputting signal from the ‘R’ pin (connected to point  403 ) or the ‘C’ pin (connected to point  402 ) at the appropriate time. 
     When the Alternating Current is flowing through the AC power booster  401 , current flow splits into two paths at circuit juncture  411 . A first path leads to the anode of the thyristor  431  and a second path leads to the resistors  422  and  423 , and the diode  424 . The resistors  422  and  423  help to refine resistance value to achieve the desired power output for the load  420 . It is appreciated that power is a function of voltage, current and resistance. Adjusting resistance helps to adjust power as well. 
     By using the similar method employed at the thyristor  231  of the DC voltage booster  202  in  FIGS. 2A and 2B , current can be refined to enhance the power output at the cathode of the thyristor  431 . In more detail, the diode  424  directs current flow in the second path towards the gate of the thyristor  431 . By sending from the microcontroller  211 , an appropriate regulating signal from the ‘R’ pin in conjunction with signals from the ‘H’ or ‘REL’ pins connected to point  405 , the thyristor  431  can be activated to allow current flow between the anode and the gate in a first instance (i.e. the holding step). By sending from the microcontroller  211 , another appropriate regulating signal from the ‘R’ pin in conjunction with signals from the ‘H’ or ‘REL’ pins connected to point  405 , the thyristor  431  can be activated to allow current flow between the gate and the cathode in a second instance (i.e. the releasing step). As a result, current and therefore voltage enhancement is provided at the cathode and the enhanced voltage at the cathode is an enhancement of the voltage at the anode. With the refined current and resistance values obtained at the cathode of the thyristor  431 , a desired AC output signal with enhanced power output is also obtained at the cathode of the thyristor  431 . The desired AC output signal is then passed to the other thyristor  432 , which is operating as a normal thyristor and in turn sent to the load  420 . 
     The resistance or current values are being monitored at the various monitoring points e.g. at points  405  and  416 . The time difference between the first instance and the second instance indicates a holding time. If during the holding time, the resistance or current values monitored at the various monitoring points e.g. at points  405  and  416  are insufficient for providing the desired power output after comparing them with predefined desirable reference resistance or current values made available to the microcontroller  211 , the holding time is delayed to hold more charge at the gate. The delay however should not be too long until the charge collected at the gate of the thyristor  431  causes thyristor  431  to reach its limit i.e. breakdown voltage at the gate. 
     Details of the AC boosting process carried out by the AC power booster  401  are described as follows with reference to  FIG. 8 . Reference is made to components in  FIG. 4 . 
     At step  801 , AC signal from the secondary winding  342  of the transformer  340  in  FIG. 3A  is received at circuit juncture  411 . More specifically, the AC signal is received by the ‘R’ pin connected to point  413 . The input voltage of the AC signal is referred to as Vac. 
     Thereafter, at step  802 , the AC signal is split into the two paths mentioned earlier at circuit juncture  411 , the first path leading towards the thyristor  431 , and the second path leading towards the resistors  422  and  423 . 
     At step  804 , the AC signal that is split at step  802  is flowing to the resistors  422  and  423 . With current under control, resistance can be adjusted to affect power. Hence, the purpose of resistors  422  and  423  is to help to adjust, in this case to gain, resistance and in the process increase or maintain the desired power required. 
     Subsequently, the current flowing to the resistors  422  and  423  at step  804  would flow to the diode  424  at step  806 . 
     After flowing to the diode  424  at step  806 , the microcontroller  411  checks at step  808  whether a calculated resistance value, R, of the incoming AC signal is at a predefined reference resistance value made available to the microcontroller  211 , which in this case is selected to be 10 ohms. It has been discovered that 10 ohms is useful for the present example. 
     It is appreciated that the predefined reference resistance value can be selected from a range of up to 200 Ohms in the present example. 
     The R value is calculated from the voltage and current values obtained from the ‘M’ pins connected to points  415 ,  416  and  404 . The I value is obtained from the ‘M’ pins connected to points  415 ,  416  and  404 . 
     If the resistance value calculated from voltage and current values read via the ‘M’ pin connected to point  404  of the microcontroller  211  is 10 ohms at step  808 , the microcontroller  211  would activate the thyristor  431  to allow current flow between the gate and the cathode of the thyristor  431  at step  810 , followed by proceeding with step  803 . 
     At step  803 , the AC signal that is split at step  802  is flowing is flowing to the thyristor  431 . 
     At step  805 , the thyristor  431  is activated by the microcontroller to allow current flow between the anode and the gate of the thyristor  431  in a first instance and between the gate and cathode of the thyristor  431  in a second instance. The holding time between the first and second instances is delayed by, for example, a microsecond, before the enhanced power in the charge at the gate of the thyristor is released at the most efficient resistance value, R, and current value, I, to the cathode of the thyristor  431 . 
     The most efficient R and I values are the predefined desirable reference resistance or current values made available to the microcontroller  211  for comparison with the calculated R value and its corresponding I value obtained from the ‘M’ pins connected to points  415 ,  416  and  404 . 
     The ‘C’ pins connected to points  414 ,  402  and  417  are put into use to direct current flow accordingly in both cases when the R and I values have reached the most efficient R and I values or when the R and I values have not reached the most efficient R and I values. 
     At step  807 , the enhanced power output acquired at step  805  is directed to the second thyristor  423  via control of the microcontroller  211  at circuit juncture  434 . The enhanced power output is then directed to drive the load  420  from the second thyristor  423 . 
     After step  807 , the process of AC power boosting carried out by the AC power booster  401  ends. 
       FIG. 10  illustrates an example of AC power boosting conducted at the AC power booster  401 . In particular, the holding step occurring in a first instance and the releasing step occurring in a second instance are illustrated. The results are obtained from observations. It is noted that although specific timings in order of microseconds, e.g. including 0.001 to 2 microseconds, are provided, they are to be regarded as estimates only and they pertain to one commercially available standard Silicon-Controlled Rectifier (SCR) thyristor. The timings may change depending on the constitution and design of the thyristor being used. It is possible to have timings longer or shorter to an extent that voltage at the cathode of the thyristor is enhanced as desired. 
     With reference to  FIG. 4 , it is assumed in  FIG. 10  that the reading at the voltage of the anode (circuit juncture  411 ) of the thyristor  431 , V A , is a sinusoidal AC voltage signal with 230-240 (i.e. root mean square voltage). The aim is to enhance the AC voltage signal at the cathode (circuit juncture  434 ) of the thyristor  431 , V C , to achieve an enhanced power output of 230-240 Vrms. In the present case, the voltage of the gate (circuit juncture  438 ), V G , follows exactly that of the voltage of the anode (circuit juncture  411 ), V A . The voltage at the cathode (circuit juncture  434 ), V C , is about 180 degrees out of phase with the voltage at the gate, V G , and at the anode, V A . For convenience, in parts of the text as follows, it is understood that the corresponding hold signal or release signal would accompany the regulating signal according to the mention of the holding step and the releasing step described earlier. All instances of rising and falling of the waveforms in  FIG. 10  are in accordance with the shape of a sine wave. 
     At the beginning, the microcontroller  211  sends a regulating signal for a period  1002  of about 0.125 microseconds. Within the period  1002 , the regulating signal begins with a pulsating wave  1003  lasting about 0.06 microseconds, which is a first time period, and pulsating between at 2 Volts and 5 Volts at about 0.02 microseconds intervals. Thereafter, the regulating signal slopes from 2 Volts to 230 Volts for about 0.0625 microseconds, which is a second time period. The pulsating wave  1003  of the period  1002  is responsible for activating the thyristor  431  to allow current flow between the anode (circuit juncture  411 ) and the gate (circuit juncture  438 ). It is appreciated that the pulsating wave  1003  may comprise one or more pulses. The pulsating wave  1003  may also be regarded as a spike and need not necessarily be square shaped as shown in  FIG. 10 . As the current flow between the anode (circuit juncture  411 ) and the gate (circuit juncture  438 ) is being established, voltage at the gate (circuit juncture  438 ), V G , begins to rise from 2 Volts to 230 Volts in the period of 1002 almost synchronously with the voltage at the anode (circuit juncture  411 ), V A . The voltage at the gate (circuit juncture  434 ), V C , falls from 230 Volts to −230 Volts during the period  1002 . It is believed that V C  is not enhanced during the period  1002 . 
     After the period  1002 , the regulating signal undergoes a period  1004  of about 0.375 microseconds, which performs the releasing step, where the thyristor  431  is activated to conduct from the gate (circuit juncture  438 ) to the cathode (circuit juncture  434 ). The waveform of the releasing step in period  1004  firstly falls generally from 230 Volts to 0 Volt for about 0.125 microseconds in a third time period but at about midway, about the 0.168 microsecond mark, there is present a fall  1005  lasting about 0.04 microseconds (i.e. a fourth time period). Thereafter, the waveform continues to fall to −230 Volts for about 0.125 microseconds. The effect of period  1004  is that the thyristor  431  releases all the charge accumulated at the gate (circuit juncture  438 ) during the period  1002  to the cathode (circuit juncture  434 ). During the period  1004 , the voltage at the cathode (circuit juncture  434 ), V C , is enhanced as it slopes from −230 Volts to 230 Volts. It is believed that the charges released runs out as V C  continues to slope from 0 Volt to 230 Volts. 
     After the period  1004 , the regulating signal undergoes another period  1006  of about 0.25 microseconds, which performs the holding step. The waveform of the holding step in period  1006  firstly rises generally from −230 Volts to 0 Volt in a fifth time period for about 0.125 microseconds but at about midway, about the 0.51 microsecond mark, there is present a rise  1007  lasting about 0.04 microseconds (i.e. a sixth time period). Thereafter, the waveform continues to rise to 230 Volts for about 0.125 microseconds. The effect of period  1006  is that it activates the thyristor  431  to accumulate and hold charge at the gate (circuit juncture  438 ). V C  drops from 230 Volts to −230 Volts during the duration of period  1006  as no charge is released to the cathode (circuit juncture  434 ). 
     After the period  1006 , the regulating signal repeats in sequence the releasing step carried out in period  1004  and the holding step carried out in period  1006  continuously to provide the desired voltage enhancement to the cathode (circuit juncture  434 ). 
     It is appreciated that the microcontroller(s) discussed herein is/are a controller or controllers for providing control over various processes of the circuits discussed herein. Other controllers similar to microcontrollers such as more rudimentary or sophisticated microprocessors or computers may also be used. It is connected to various components of the circuits, either directly or through Integrated Circuits (i.e. IC 1   370  and IC 2   380 , which can be microcontrollers and the like as well), or through conducting wires running through a Printed Circuit Board. A program written in Programmable Integrated Control (PIC) language (i.e. a type of assembly language) is programmed into the microcontroller(s) to enable the microcontroller(s) or Integrated Circuits to monitor and command various activities taking place at various points within the circuits. The communication between the microcontroller(s) and the components is in the form of electronic waves passing through the conducting wires. The microcontroller(s) being used in the circuits discussed herein may have 40 pins. Each pin or group of pins may monitor or command designated functions at specific points in the circuits. The Integrated Circuits may each have 8 pins. The PIC program could have about 68,356 lines of code and have a minimum response time in the execution of the codes that is measured in micro-seconds so as to keep up with the steps of the method steps discussed herein. 
     It is further appreciated that all circuit points mentioned herein refers to a selected current conducting point of interest in a circuit. All circuit junctures mentioned herein refers to a region of interest in a circuit, which includes one or more circuit points. Connection or coupling to a circuit juncture refers to connection to one or more of the circuit points in the circuit juncture. When a circuit juncture inputs or outputs current or signal, it means that one or more of the circuit points in the circuit juncture are involved in inputting or outputting the current or signal. 
     Many modifications can be made to the apparatus and the method for enhancing power output by those skilled in the art having the understanding of the above described disclosure together with the drawings. Therefore, it is to be understood that the apparatus and the method for enhancing power output is not to be limited to the above description contained herein only.