Patent Publication Number: US-2020305252-A1

Title: Circuit for supplying power to components of lighting apparatus, and lighting apparatus including the same

Description:
RELATED APPLICATIONS 
     The present application is a national stage application under 35 U.S.C. § 371 of International Application PCT/KR2018/003009, filed on Mar. 14, 2018, which claims priority to and the benefit of Korean Patent Application No. 10-2017-0134813 filed on Oct. 17, 2017. The entire content of the aforementioned applications are incorporated in their entirety herein by reference. 
    
    
     TECHNICAL FIELD 
     The disclosure relates to a power supply circuit, and more particularly, to a power supply circuit included in a lighting apparatus and a lighting apparatus including the power supply circuit. 
     BACKGROUND ART 
     Light-emitting diodes (LEDs) are being used in various applications because of their superior power consumption characteristic and smaller size than other light sources. Due to the characteristics of an LED of which light intensity depends on the magnitude of a current passing therethrough, a lighting apparatus using an AC voltage as a power source of an LED may include a component for converting the AC voltage. Furthermore, recently, a lighting apparatus may include peripheral components for performing operations such as brightness control, turning on/off, and color temperature control, in response to an external control or a surrounding environment. Since the power requirement for driving LEDs and the power requirement for driving peripheral components are different, a method of efficiently satisfying the power requirements of both is needed. 
     DESCRIPTION OF EMBODIMENTS 
     TECHNICAL PROBLEM 
     The disclosure provides a circuit for efficiently supplying power to a peripheral component in a lighting apparatus including a light-emitting diode (LED) and a lighting apparatus including the circuit. 
     SOLUTION TO PROBLEM 
     According to an aspect of the disclosure, there is provided an apparatus comprising a regulator circuit configured to generate at least one positive supply voltage from at least a portion of an LED driving current passed through a light emitting diode (LED) to supply power to components included in a lighting apparatus; and a converter circuit configured to receive a first control signal from the component and output a second control signal for controlling the LED driving current by converting the first control signal. 
     According to an example embodiment of the disclosure, the regulator circuit may include a shunt regulator that generates a first positive supply voltage from at least a part of the LED driving current. 
     According to an example embodiment of the disclosure, the apparatus may further include a dimming off detector configured to detect a dimming off state based on the first control signal or the second control signal; and a current supply circuit configured to provide a current generated from a full-wave rectified input voltage from an alternating current (AC) voltage to the regulator circuit, according to the detected dimming off state. 
     According to an example embodiment of the disclosure, according to the detected dimming off state, the shunt regulator may be turned off and a current provided by the current supply circuit may be provided to a node for outputting the first positive supply voltage. 
     According to an example embodiment of the disclosure, the regulator circuit may include a linear regulator configured to generate a second positive supply voltage from the first positive supply voltage. 
     According to an example embodiment of the disclosure, the regulator circuit may include a reference circuit configured to generate a reference signal provided to at least one of the shunt regulator and the linear regulator from the first positive supply voltage. 
     According to an example embodiment of the disclosure, the converter circuit may convert the first control signal having a variable voltage into the second control signal having one of a variable current, a variable voltage, and a variable light intensity. 
     According to an example embodiment of the disclosure, the converter circuit may output the second control signal at a certain level when the first control signal exceeds a preset upper bound. 
     According to an example embodiment of the disclosure, the converter circuit may output the second control signal at a certain level when the first control signal is below a preset lower bound. 
     According to an example embodiment of the disclosure, the apparatus may further include an LED driver configured to generate, from an input voltage, the LED driving current having a magnitude that follows the magnitude of the input voltage full-wave rectified from an AC voltage and to adjust the magnitude of the LED driving current based on the second control signal. 
     According to an example embodiment of the disclosure, the LED driver may include a current supply circuit configured to provide a supplementary current generated from the input voltage to the regulator circuit based on the second control signal. 
     According to an example embodiment of the disclosure, the apparatus may further include the component configured to receive power from the at least one positive supply voltage and to generate the first control signal from an external signal received from the outside of the lighting apparatus. 
     According to another aspect of the disclosure, there is provided a lighting apparatus configured to receive an alternating current (AC) voltage from the outside, the lighting apparatus including an LED array including at least one LED; an LED driver configured to provide an LED driving current to the LED array; a regulator circuit configured to generate at least one positive supply voltage from at least a portion of the LED driving current passed through the LED array; and a digital circuit configured to receive power from the at least one positive supply voltage. 
     According to an example embodiment of the disclosure, the component may generate a first control signal for controlling the lighting apparatus based on an external signal input from the outside of the lighting apparatus, the lighting apparatus may further include a converter circuit configured to output a second control signal for controlling the LED driving current by converting the first control signal, and the LED driver may adjust the LED driving current based on the second control signal. 
     According to an example embodiment of the disclosure, the LED array may include a plurality of LED sub-arrays including LEDs of different color temperatures, and the LED driver may adjust the LED driving current supplied to each of the plurality of LED sub-arrays based on the second control signal. 
     According to an example embodiment of the disclosure, the component may include an interface circuit configured to receive the external signal through a communication channel. 
     According to an example embodiment of the disclosure, the component may include a sensor configured to obtain the external signal from an environment outside the lighting apparatus. 
     ADVANTAGEOUS EFFECTS OF DISCLOSURE 
     According to an example embodiment of the disclosure, a circuit for supplying power to a component included in a lighting apparatus and a lighting apparatus including the circuit may significantly reduce power consumption, space occupancy, cost, etc., due to an element for generating a positive supply voltage. 
     Furthermore, according to an example embodiment of the disclosure, a circuit for supplying power to a component included in a lighting apparatus and a lighting apparatus including the circuit may improve power efficiency for generating a positive supply voltage. 
     Furthermore, according to an example embodiment of the disclosure, a circuit for supplying power to a component included in a lighting apparatus and a lighting apparatus including the circuit may not only enables miniaturization the lighting apparatus, but also facilitate implementation of a lighting apparatus supporting various active operations. 
     The effects obtainable in the example embodiments of the disclosure are not limited to the above-mentioned effects, and other effects not mentioned above may be clearly derived and understood by one of ordinary skill in the art from the following descriptions. In other words, unintended effects of practicing example embodiments of the disclosure may also be derived by one of ordinary skilled in the art from the example embodiments of the disclosure. 
    
    
     
       BRIEF DESCRIPTION OF DRAWINGS 
         FIGS. 1A and 1B  are block diagrams showing lighting apparatuses according to comparative examples of example embodiments of the disclosure. 
         FIG. 2  is a block diagram showing a lighting apparatus according to an example embodiment of the disclosure. 
         FIG. 3  is a block diagram showing examples of a power delivery circuit and a peripheral component of  FIG. 2  according to an example embodiment of the disclosure. 
         FIG. 4  is a block diagram showing an example of a regulator circuit of  FIG. 3  according to an example embodiment of the disclosure. 
         FIGS. 5A to 5C  are circuit diagrams showing examples of a shunt regulator of  FIG. 4  according to example embodiments of the disclosure. 
         FIG. 6  is a block diagram showing examples of peripheral components and a converter circuit of  FIG. 3  according to an example embodiment of the disclosure. 
         FIGS. 7A to 7C  are graphs showing examples of the operation of a limiter of  FIG. 6  according to example embodiments of the disclosure. 
         FIG. 8A  is a diagram showing an example of an LED driver of  FIG. 2  according to an example embodiment of the disclosure, and  FIG. 8B  is a diagram showing an example of the operation of an LED driver of  FIG. 8A  according to an example embodiment of the disclosure. 
         FIG. 9  is a diagram showing an example of the LED driver of  FIG. 2  according to an example embodiment of the disclosure. 
         FIGS. 10A and 10B  are circuit diagrams showing examples of a current supply circuit of  FIG. 9  according to example embodiments of the disclosure. 
         FIG. 11  is a block diagram showing an example of the LED driver of  FIG. 2  according to an example embodiment of the disclosure. 
         FIG. 12  is a block diagram showing an example of the power delivery circuit of  FIG. 2  according to an example embodiment of the disclosure. 
         FIGS. 13A to 13C  are circuit diagrams showing examples of the shunt regulator of  FIG. 4  according to example embodiments of the disclosure. 
         FIGS. 14A to 14C  are diagrams showing examples of reducing power consumption of the lighting apparatus of  FIG. 2  in a standby state according to example embodiments of the disclosure. 
         FIG. 15A  is a diagram showing an example of the LED driver of  FIG. 2  according to an example embodiment of the disclosure, and  FIG. 15B  is a diagram showing an example of a current supply circuit of  FIG. 15A  according to an example embodiment of the disclosure. 
         FIG. 16A  is a diagram showing an example of the power delivery circuit of  FIG. 2  according to an example embodiment of the disclosure, and  FIG. 16B  is a diagram showing an example of a dimming-off current supply circuit of  FIG. 16A  according to an example embodiment of the disclosure. 
         FIGS. 17A to 17C  are diagrams showing examples of operations of a power delivery circuit of  FIG. 16A  and the dimming-off current supply circuit of  FIG. 16B , according to example embodiments of the disclosure. 
         FIGS. 18A and 18B  are block diagrams showing examples of a lighting apparatus according to example embodiments of the disclosure. 
         FIG. 19  is a flowchart of a method of supplying power to a peripheral component in a lighting apparatus including LEDs according to an example embodiment of the disclosure. 
         FIGS. 20A and 20B  are diagrams showing lighting apparatuses according to example embodiments of the disclosure. 
         FIG. 21  is a diagram showing a home network including a lighting apparatus according to an example embodiment of the disclosure. 
     
    
    
     MODE OF DISCLOSURE 
     Hereinafter, example embodiments will be described in detail with reference to the accompanying drawings. Example embodiments are provided to more fully explain the disclosure to one of ordinary skill in the art. The disclosure may include various embodiments and modifications, and embodiments thereof will be illustrated in the drawings and will be described herein in detail. However, this is not intended to limit the disclosure to particular modes of practice, and it is to be appreciated that all changes, equivalents, and substitutes that do not depart from the spirit and technical scope of the disclosure are encompassed in the disclosure. Like reference numerals are used for similar elements in describing each drawing. In the accompanying drawings, the dimensions of the structures are shown enlarged or reduced from the actual size for the sake of clarity of the inventive concept. 
     The terms used in the present specification are merely used to describe particular embodiments, and are not intended to limit the disclosure. An expression used in the singular encompasses the expression of the plural, unless it has a clearly different meaning in the context. In the present specification, it is to be understood that the terms such as “including” or “having,” etc., are intended to indicate the existence of the features, numbers, steps, actions, components, parts, or combinations thereof disclosed in the specification, and are not intended to preclude the possibility that one or more other features, numbers, steps, actions, components, parts, or combinations thereof may exist or may be added. 
     Unless otherwise defined, all terms used herein, including technical or scientific terms, have the same meaning as commonly understood by one of ordinary skill in the art to which the disclosure belongs. Terms identical to those defined in commonly used dictionaries should be interpreted as having a meaning consistent with the meaning in the context of the related art and are not to be interpreted as ideal or overly formal in meaning unless explicitly defined in the present application. 
       FIGS. 1A and 1B  are block diagrams showing lighting apparatuses according to comparative examples of example embodiments of the disclosure. Lighting apparatuses  10   a  and  10   b  may include LED arrays  16   a  and  16   b  as light sources, and power may be supplied to the LED arrays  16   a  and  16   b  from an AC voltage V_AC. A lighting apparatus  10   a  of  FIG. 1A  may include an AC/DC converter  13   a  to provide a positive supply voltage V_DD to a peripheral component  14   a,  while a lighting apparatus  10   b  of  FIG. 1B  may include a linear regulator  13   b  to provide a positive supply voltage V_DD to a peripheral component  14   b.  Hereinafter, redundant descriptions of  FIGS. 1A and 1B  will be omitted. 
     Referring to  FIG. 1A , the lighting apparatus  10   a  may include an EMI filter  11   a,  a full-wave rectifier  12   a,  the AC/DC converter  13   a,  the peripheral component  14   a,  an LED driver  15   a,  and an LED array  16   a.  The EMI filter  11   a  may receive the AC voltage V_AC and may remove a high frequency component due to a switching current generated from the AC/DC converter  13   a.  The full-wave rectifier  12   a  may generate an input voltage V_IN having a full-wave rectified potential with respect to a ground potential GND from the AC voltage V_AC, such as a sine wave. As shown in  FIG. 1A , the input voltage V_IN generated by the full-wave rectifier  12   a  may be provided to the AC/DC converter  13   a  and the LED driver  15   a.    
     The AC/DC converter  13   a  may generate the positive supply voltage V_DD for the peripheral component  14   a  from the input voltage V_IN. In order to generate the positive supply voltage V_DD, which is a direct voltage of several volts, the AC/DC converter  13   a  may include a transformer or an inductor, a large capacitor, a switch such as a power transistor, and a control integrated circuit for switching control. Accordingly, the AC/DC converter  13   a  may have a large volume and consequently limit the miniaturization of the lighting apparatus  10   a,  and the EMI filter  11   a  for the AC/DC converter  13   a  may also limit the miniaturization of the lighting apparatus  10   a.  Also, the AC/DC converter  13   a  generates the positive supply voltage V_DD of several volts (e.g., 5V, 3.3V, etc.) from the input voltage V_IN of tens to hundreds of volts (e.g., 220 Vrms), and thus the power efficiency of the AC/DC converter  13   a  may be low. For example, power lost due to low power efficiency may be converted into heat energy and released, thereby degrading the characteristics of the lighting apparatus  10   a,  and luminance per power (lm/W) as a specification of the lighting apparatus  10   a  may decrease. 
     The peripheral component  14   a  may receive power from the AC/DC converter  13   a  through the positive supply voltage V_DD, generate a control signal CTR, and transmit the generated control signal CTR to the LED driver  15   a.  For example, the peripheral component  14   a  may adjust the intensity of light emitted by the LED array  16   a  via the control signal CTR. 
     The LED driver  15   a  may generate an LED driving current I_LED from the input voltage V_IN and may provide the LED driving current I_LED to the LED array  16   a  including a plurality of LEDs. The LED driver  15   a  may adjust the LED driving current I_LED provided to the LED array  16   a  in response to the control signal CTR. 
     Referring to  FIG. 1B , the lighting apparatus  10   b  may include a full-wave rectifier  12   b,  a linear regulator  13   b,  a peripheral component  14   b,  an LED driver  15   b,  and an LED array  16   b.  As shown in  FIG. 1B , to provide the positive supply voltage V_DD to the peripheral component  14   b,  the linear regulator  13   b  may generate the positive supply voltage V_DD from the input voltage V_IN that is full-wave rectified from the AC voltage V_AC. Since the linear regulator  13   b  generates the positive supply voltage V_DD of several volts from the input voltage V_IN of tens to hundreds of volts, due to the power loss at the linear regulator  13   b,  the linear regulator  13   b  may provide significantly low power efficiency. Power loss occurring at the linear regulator  13   b  may be released as heat, thereby not only degrading the characteristics of the lighting apparatus  10   b,  but also causing malfunction or failure of the linear regulator  13   b.    
     As described above with reference to  FIGS. 1A and 1B , in the lighting apparatuses  10   a  and  10   b  including the peripheral components  14   a  and  14   b,  elements that generates the positive supply voltage V_DD from the input voltage V_IN, which is full-wave rectified from the AC voltage V_AC, or the AC voltage V_AC may degrade the characteristics of the lighting apparatuses  10   a  and  10   b.  Therefore, the inclusion of the peripheral components  14   a  and  14   b  in the lighting apparatus  10   a  and  10   b  may be limited, and as a result, the implementation of the lighting apparatuses  10   a  and  10   b  that provide various functions may be limited. 
     As will be described below with reference to the drawings, a circuit for supplying power to peripheral circuits and an apparatus including the same according to example embodiments of the disclosure may significantly reduce heat generation, space occupancy, and cost due to components for generating a positive supply voltage to be provided to the peripheral circuits. Also, a circuit for supplying power to peripheral circuits and an apparatus including the same according to example embodiments of the disclosure may improve the power efficiency for generating a positive supply voltage, miniaturize a lighting apparatus, and facilitate the implementation of a lighting apparatus supporting various active operations. 
       FIG. 2  is a block diagram showing a lighting apparatus  100  according to an example embodiment of the disclosure. 
     The lighting apparatus  100  may include an LED array  160  as a light source, and as a non-limiting example, may be included in a lamp for indoor lighting, outdoor lighting, portable lighting, vehicle lighting, etc. In some embodiments, the lighting apparatuses  10   a  and  10   b  may be independently distributed units and may be removed from lamps. As shown in  FIG. 2 , the lighting apparatus  100  may receive power from the AC voltage V_AC and may include a full-wave rectifier  120 , a power delivery circuit  130 , a peripheral component  140 , an LED driver  150 , and the LED array  160 . In some embodiments, two or more elements included in the lighting apparatus  100  may be included in one semiconductor package. For example, the power delivery circuit  130 , the peripheral component  140 , and the LED driver  150  may be included in one semiconductor package, two or more from the power delivery circuit  130 , the peripheral component  140 , and the LED driver  150  may be included in one semiconductor package, or the power delivery circuit  130 , the peripheral component  140 , and the LED driver  150  may be respectively included in different semiconductor packages. 
     The full-wave rectifier  120  may generate the input voltage V_IN having a full-wave rectified potential with respect to the ground potential GND from the AC voltage V_AC, such as a sine wave. As shown in  FIG. 2 , the input voltage V_IN may be provided to the LED driver  150 , and the power delivery circuit  130  and the peripheral component  140  may be connected to the ground potential GND. 
     The LED array  160  may include at least one LED and may be configured as at least one LED string including serially connected LEDs. In some embodiments, the LED array  160  may include at least one LED having substantially the same color temperature and may also include a plurality of LEDs each having two or more different color temperatures. Each of LED strings included in the LED array  160  may receive at least a part of the LED driving current I_LED, and the intensity of emitted light may be determined according to the amount of current passing through a corresponding LED string. 
     The LED driver  150  may generate the LED driving current I_LED from the input voltage V_IN and provide the LED driving current I_LED to the LED array  160 . Also, as shown in  FIG. 2 , the LED driver  150  may receive the LED driving current I_LED that passed through the LED array  160 . The LED driver  150  may provide at least a portion I_LED′ of the LED driving current I_LED to the power delivery circuit  130 . In some embodiments, the current I_LED′ may be substantially the same as the LED driving current I_LED. In some embodiments, the current I_LED′ may coincide with currents passed through some LED strings, e.g., some LED sub-arrays, of the LED array  160 . As described below, the positive supply voltage V_DD of the peripheral component  140  may be generated from at least the portion I_LED′ of the LED driving current I_LED provided to the power delivery circuit  130 . Also, the LED driver  150  may adjust the LED current I_LED based on a second control signal CTR 2  received from the power delivery circuit  130 . Examples of the LED driver  150  will be described below with reference to  FIGS. 8A, 8B, 9, and 11 . 
     The power delivery circuit  130  may receive at least a portion I_LED′ of the LED driving current I_LED from the LED driver  150 , generate the positive supply voltage V_DD from the current I_LED′, and generate the positive supply voltage V_DD to the peripheral component  140 . In other words, as the power source of the peripheral components  140 , the positive supply voltage V_DD may be generated from at least the part I_LED′ of the LED driving currents I_LED used by the LED array  160  to emit light instead of being generated directly from the input voltage V_IN,. A node through which the current I_LED′ moves from the LED driver  150  to the power delivery circuit  130  may have a voltage decreased from the input voltage V_IN based on to a voltage drop due to the LED driver  150  and the LED array  160 . Therefore, as described above with reference to  FIGS. 1A and 1B , to generate the positive supply voltage V_DD from the input voltage V_IN, the positive supply voltage V_DD for the peripheral component  140  may be easily generated without using components inferior in terms of volume, heat generation, and power efficiency (e.g.,  13   a  of  FIG. 1A and 13   b  of  FIG. 1B ). 
     As shown in  FIG. 2 , the power delivery circuit  130  may receive a first control signal CTR 1  for controlling the lighting apparatus  100  from the peripheral components  140  and may generate and provide the second control signal CTR 2  for controlling the LED driving current I_LED to the LED driver  150  by converting the first control signal CTR 1 . The first control signal CTR 1  output from the peripheral component  140  may have a voltage between the positive supply voltage V_DD and the ground potential GND, and thus the power delivery circuit  130  may generate the second control signal CTR 2  that may be detected by the LED driver  150  by converting the first control signal CTR 1 . Examples of the power delivery circuit  130  will be described below with reference to  FIG. 3 . 
     The peripheral component  140  may operate based on power provided by the positive supply voltage V_DD and may generate the first control signal CTR 1 . For example, the peripheral component  140  may include digital and/or analog circuit(s) that receive(s) the positive supply voltage V_DD. 
     In some embodiments, the peripheral component  140  may generate the first control signal CTR 1  based on an external signal received via a wired or wireless communication channel with an external device. For example, the peripheral components  140  may include, as a non-limiting example, a module for a communication via a wire, such as a universal serial bus (USB), a power line communication (PLC), or the like, and may include, as a non-limiting example, a module for a wireless communication such as Bluetooth, ZigBee, TV white space (TVWS), Wi-Fi, or the like. A communication module included in the peripheral component  140  may operate by the positive supply voltage V_DD, and the first control signal CTR 1  may be generated based on a command received from the outside through a communication channel. 
     In some embodiments, the peripheral component  140  may generate the first control signal CTR 1  by sensing the environment outside the lighting apparatus  100 . For example, the peripheral component  140  may include, as a non-limiting example, a sensor that converts a sensed external signal into an electrical signal, such as a temperature sensor, an luminance sensor, a motion sensor, an infrared sensor, a microphone, and the like, and the first control signal CTR 1  may be generated based on an output signal of the sensor. 
     In some embodiments, the peripheral component  140  may generate the first control signal CTR 1  internally. For example, the peripheral component  140  may include, as a non-limiting example, a timer and may generate the first control signal CTR 1  based on an output of the timer. 
       FIG. 3  is a block diagram showing examples of the power delivery circuit  130  and the peripheral component  140  of  FIG. 2  according to an example embodiment of the disclosure. As shown in  FIG. 3 , a power delivery circuit  130 ′ may provide the positive supply voltage V_DD to a peripheral component  140 ′, and the peripheral component  140 ′ may provide the first control signal CTR 1  to the power delivery circuit  130 ′. Hereinafter,  FIG. 3  will be described with reference to  FIG. 2 . 
     Referring to  FIG. 3 , the power delivery circuit  130 ′ may include a regulator circuit  132  and a converter circuit  134 . The regulator circuit  132  may generate the positive supply voltage V_DD from the current I_LED′ provided from the LED driver  150  of  FIG. 2 . As shown in  FIG. 3 , a capacitor C_OUT may be provided between a node, through which the positive supply voltage V_DD is transmitted from the regulator circuit  132  to the peripheral component  140 ′, and the ground potential GND, and the capacitor C_OUT may provide an instantaneous load current occurring in the peripheral component  140 ′. An example of the regulator circuit  132  will be described below with reference to  FIG. 4 . 
     The converter circuit  134  may generate the second control signal CTR 2  by converting the first control signal CTR 1 , and provide the second control signal CTR 2  to the LED driver  150  of  FIG. 2 . In some embodiments, the converter circuit  134  may generate the second control signal CTR 2  having a variable voltage or a variable current by converting the first control signal CTR 1  having a variable voltage. In other words, the converter circuit  134  may serve as a voltage-voltage converter or a voltage-current converter. On the other hand, the converter circuit  134  may generate the second control signal CTR 2 , which is a non-electrical signal (e.g., an optical signal), by converting the first control signal CTR 1 , which is an electrical signal. An example of the converter circuit  134  will be described below with reference to  FIG. 6 . 
       FIG. 4  is a block diagram showing an example of the regulator circuit  132  of  FIG. 3  according to an example embodiment of the disclosure. As described above with reference to  FIG. 3 , a regulator circuit  132 ′ of  FIG. 4  may generate the positive supply voltage V_DD from the current I_LED′ provided from the LED driver  150  of  FIG. 2 . As shown in  FIG. 4 , the regulator circuit  132 ′ may generate a plurality of positive supply voltages V_DD 1 , V_DD 2 , and V_DD 3  and may include a shunt regulator  132 _ 2 , a reference circuit  132 _ 4 , and linear regulators  132 _ 6  and  132 _ 8 . Although  FIG. 4  shows an example in which the regulator circuit  132 ′ includes two linear regulators  132 _ 6  and  132 _ 8 , a regulator circuit may include one linear regulator, may include or three or more linear regulators, or may include no linear regulator according to example embodiments of the disclosure. 
     The shunt regulator  132 _ 2  may adjust the supply of a current to a load to maintain a first positive supply voltage V_DD 1  constant. In other words, the shunt regulator  132 _ 2  may provide the first positive supply voltage V_DD 1  by adjusting the magnitude of current which flows as a portion of the current I_LED′ toward the ground potential GND. As shown in  FIG. 4 , the first positive supply voltage V_DD 1  generated by the shunt regulator  132 _ 2  may be provided to other components of the regulator circuit  132 ′. Therefore, the shunt regulator  132 _ 2  may be referred to as a master regulator, and the linear regulators  132 _ 6  and  132 _ 8  may be referred to as slave regulators. Examples of the shunt regulator  132 _ 2  will be described below with reference to  FIGS. 5A to 5C . 
     The reference circuit  132 _ 4  may generate a reference signal REF from the first positive supply voltage V_DD 1 . In some embodiments, the reference signal REF may be a reference current having a preset magnitude. In some embodiments, the reference signal REF may be a reference voltage having a preset magnitude. In some embodiments, the reference circuit  132 _ 4  may generate both a reference current and a reference voltage. As shown in  FIG. 4 , the reference signal REF may be provided to other regulators, that is, the shunt regulator  132 _ 2  and the linear regulators  132 _ 6  and  132 _ 8 . 
     In some embodiments, the reference circuit  132 _ 4  may receive the input voltage V_IN of  FIG. 2 . For example, when the magnitude of the first positive supply voltage V_DD 1  is not sufficient to generate the reference signal REF, the reference circuit  132 _ 4  may generate the reference signal REF from the input voltage V_IN. 
     The linear regulators  132 _ 6  and  132 _ 8  may receive the first positive supply voltage V_DD 1  and the reference signal REF and generate positive supply voltages V_DD 2  and V_DD 3 . In other words, the first linear regulator  132 _ 6  may generate a second positive supply voltage V_DD 2 , and the second linear regulator  132 _ 8  may generate a third positive supply voltage V_DD 3 . The linear regulators  132 _ 6  and  132 _ 8  may have high efficiency of generating second and third positive supply voltages V_DD 2  and V_DD 3  from the first positive supply voltage V_DD 1  of several volts provided by the shunt regulator  132 _ 2 . 
       FIGS. 5A to 5C  are circuit diagrams showing examples of the shunt regulator  132 _ 2  of  FIG. 4  according to example embodiments of the disclosure. As described above with reference to  FIG. 4 , shunt regulators  132 _ 2   a,    132 _ 2   b,  and  132 _ 2   c  of  FIGS. 5A to 5C  may generate the first positive supply voltage V_DD 1  from the current I_LED′ provided from the LED driver  150  of  FIG. 2 . The shunt regulators  132 _ 2   a,    132 _ 2   b,  and  132 _ 2   c  of  FIGS. 5A to 5C  are merely examples, and it will be understood that a shunt regulator having a different structure from those of the shunt regulators  132 _ 2   a,    132 _ 2   b , and  132 _ 2   c  may be used. 
     Referring to  FIG. 5A , the shunt regulator  132 _ 2   a  may include a zener diode Z 51 . Therefore, the first positive supply voltage V_DD 1  may substantially match the breakdown voltage of the zener diode Z 51 . In other words, as shown in  FIG. 5A , the current I_LED′ may be branched into a load current I_LOAD and a shunt current I_SHUNT. In the zener diode Z 51 , when the load current I_LOAD increases, the shunt current I_SHUNT may decrease as much as the increase of the load current I_LOAD, and thus the first positive supply voltage V_DD 1  may be maintained constant. In the same regard, when the load current I_LOAD decreases, the shunt current I_SHUNT may increase as much as the decrease of the load current I_LOAD, and thus the first positive supply voltage V_DD 1  may be maintained constant. As shown in  FIG. 5A , a capacitor C 51   a  may be connected to an output node of a shunt regulator  132 _ 2   a,  that is, a node that outputs the first positive supply voltage V_DD 1 . 
     Referring to  FIG. 5B , a shunt regulator  132 _ 2   b  may include an operational amplifier A 51 , an NMOS transistor N 51 , and resistors R 51  and R 52 . Therefore, the first positive supply voltage V_DD 1  may be determined as shown in [Equation 1] below. 
     
       
         
           
             
               
                 
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                     1 
                   
                   ] 
                 
               
             
           
         
       
     
     The first positive supply voltage V_DD 1  may be determined by the reference voltage V_REF and the resistors R 51  and R 52  according to [Equation 1]. In some embodiments, the reference voltage V_REF may be provided from the reference circuit  132 _ 4  of  FIG. 4 . In some embodiments, the reference voltage V_REF may be generated inside the shunt regulator  132 _ 2   b.  Also, in some embodiments, a bipolar npn transistor may be used instead of the NMOS transistor N 51 . Similar to the shunt regulator  132 _ 2   a  of  FIG. 5A , a capacitor C 51   b  may be connected to an output node of the shunt regulator  132 _ 2   b,  that is, a node that outputs the first positive supply voltage V_DD 1 . 
     Referring to  FIG. 5C , a shunt regulator  132 _ 2   c  may include an operational amplifier A 52 , a PMOS transistor P 51 , and the resistors R 51  and R 52 . Accordingly, the first positive supply voltage V_DD 1  may be determined by the reference voltage V_REF and the resistors R 51  and R 52  as shown in [Equation 1] above. In some embodiments, the reference voltage V_REF may be provided from the reference circuit  132 _ 4  of  FIG. 4 . In some embodiments, the reference voltage V_REF may be generated inside the shunt regulator  132 _ 2   c.  Also, in some embodiments, a bipolar pnp transistor may be used instead of the PMOS transistor P 51 . Similar to the shunt regulator  132 _ 2   a  of  FIG. 5A , a capacitor C 51   c  may be connected to an output node of the shunt regulator  132 _ 2   c,  that is, a node that outputs the first positive supply voltage V_DD 1 . 
     Referring to  FIGS. 5B and 5C , the shunt regulators  132 _ 2   b  and  132 _ 2   c  are controlled by the operational amplifiers A 51  and A 52 , such that the current of the NMOS transistor N 51  or the PMOS transistors P 51  decreases or increases as the load current increases or decreases. Therefore, the first positive supply voltage V_DD 1  may be determined as shown in [Equation 1]. 
       FIG. 6  is a block diagram showing examples of the peripheral components  140 ′ and the converter circuit  134  of  FIG. 3  according to an example embodiment of the disclosure. As described above with reference to  FIG. 3 , a peripheral component  140 ″ of  FIG. 6  may generate the first control signal CTR 1  from an external signal EXT, and the converter circuit  134 ′ may generate the second control signal CTR 2  from the first control signal CTR 1 . 
     Referring to  FIG. 6 , the peripheral components  140 ″ may include a controller  142  and a filter  144 . The controller  142  may receive the external signal EXT generated outside the lighting apparatus  100  of  FIG. 2  and generate a pulse width modulation (PWM) signal PWM from the external signal EXT. For example, the controller  142  may generate a PWM signal PWM for adjusting the intensity of light emitted by the lighting apparatus  100  in response to the external signal EXT, and a positive pulse width or a negative pulse width of the PWM signal PWM may increase in proportion to the light intensity. 
     The filter  144  may generate the first control signal CTR 1  by filtering the PWM signal PWM. For example, the filter  144  may low-pass filter the PWM signal PWM, thereby generating the first control signal CTR 1  having a voltage proportional to the positive pulse width of the PWM signal PWM. The filter  144  may, in some embodiments, include passive devices such as resistors and capacitors. 
     Also, in some embodiments, the controller  142  may generate an analog signal for adjusting the intensity of light emitted by the lighting apparatus  100  in response to the external signal EXT, wherein the analog signal may increase in proportion to the intensity of the light. In this case, the filter  144  may be omitted. 
     Referring to  FIG. 6 , a converter circuit  134 ′ may include a limiter  134 _ 2  and a converter  134 _ 4 . The limiter  134 _ 2  may generate a limited signal LIM by limiting the first control signal CTR 1  to a preset range. For example, the limiter  134 _ 2  may have a preset upper bound and/or a preset lower bound according to a variable range of brightness and may generate the limited signal LIM by comparing the first control signal CTR 1  with the upper bound and/or the lower bound. Example operations of the limiter  134 _ 2  will be described below with reference to  FIGS. 7A to 7C . 
     The converter  134 _ 4  may generate the second control signal CTR 2  by converting the limited signal LIM. In some embodiments, the first control signal CTR 1  and the limited signal LIM may have voltages that varies according to information contained therein, and the converter  134 _ 4  may generate the second control signal CTR 2  having a variable current from the limited signal LIM having a variable voltage. In other words, converter  134 _ 4  may function as a voltage-current converter. As described above with reference to  FIG. 2 , the second control signal CTR 2  may be provided to the LED driver  150 , and the LED driver  150  may have a reference potential different from that of the peripheral components  140 . Therefore, the limited signal LIM may be converted by the converter  134 _ 4 , such that the signal CTR 2  has a variable current. 
     In some embodiments, the first control signal CTR 1  and the limited signal LIM may have voltages that varies according to information contained therein, and the converter  134 _ 4  may generate the second control signal CTR 2  having a variable voltage based on the positive supply voltage V_DD from the limited signal LIM having a variable voltage. In other words, converter  134 _ 4  may function as a voltage-voltage converter. As described above with reference to  FIG. 2 , the second control signal CTR 2  may be provided to the LED driver  150 , and the LED driver  150  may have a reference potential different from that of the peripheral components  140 . Therefore, the limited signal LIM may be converted by the converter  134 _ 4 , such that the signal CTR 2  has a variable voltage. 
       FIGS. 7A to 7C  are graphs showing examples of the operation of a limiter  134 _ 2  of  FIG. 6  according to example embodiments of the disclosure. As described above with reference to  FIG. 6 , the limiter  134 _ 2  may generate the limited signal LIM by limiting the first control signal CTR 1  based on a preset upper bound and/or a preset lower bound. In  FIGS. 7A to 7C , it is assumed that the first control signal CTR 1  and the limited signal LIM have variable voltages, and the horizontal axis and the vertical axis of the graphs indicate the magnitudes of voltages. 
     Referring to  FIG. 7A , the limiter  134 _ 2  may have an upper bound V_UB and may generate the limited signal LIM having a constant voltage V 1   a  when the magnitude of the first control signal CTR 1  exceeds the upper bound V_UB. The upper bound V_UB may be determined based on a range of the second control signal CTR 2  that may be acceptable by the LED driver  150  of  FIG. 2 . 
     Referring to  FIG. 7B , the limiter  134 _ 2  may have the upper bound V_UB and a lower bound V_LB, may generate the limited signal LIM having a constant voltage V 1   b  when the magnitude of the first control signal CTR 1  exceeds the upper bound V_UB, and may generate the limited signal LIM having an approximately zero magnitude when the magnitude of the first control signal CTR 1  is smaller than the lower bound V_LB. In other words, when the magnitude of the first control signal CTR 1  is smaller than the preset lower bound V_LB, the limiter  134 _ 2  may generate a limited signal LIM having an approximately zero magnitude, such that the lighting apparatus  100  of  FIG. 2  is turned off, that is, no light is emitted from the LED array  160 . 
     Referring to  FIG. 7C , the limiter  134 _ 2  may have the upper bound V_UB and the lower bound V_LB, may generate the limited signal LIM having a constant voltage V 1   c  when the magnitude of the first control signal CTR 1  exceeds the upper bound V_UB, and may generate the limited signal LIM having a constant voltage V 2   c  when the magnitude of the first control signal CTR 1  is lower than the lower bound V_LB. In other words, unlike in the example of  FIG. 7B , when the magnitude of the first control signal CTR 1  is smaller than the preset lower bound V_LB, the limiter  134 _ 2  may generate the limited signal LIM having the constant voltage V 2   c,  such that light of a constant intensity is emitted from the LED array  160  of  FIG. 2 . 
     In some embodiments, the limiter  134 _ 2  of the converter circuit  134 ′ may be omitted. Referring to  FIG. 2 , the LED driver  150  may include a limiter that operates similarly as the limiter  134 _ 2 . Also, the converter circuit  134 ′ may provide the second control signal CTR 2  to the LED driver  150  by only converting the first control signal CTR 1  without limitations of an upper bound and a lower bound. In some embodiments, the functions of the limiter  134 _ 2  to limit the lower bound and the upper bound of the first control signal CTR 1  may be implemented separately in the converter circuit  134 ′ and the LED driver  150 , respectively. For example, the first control signal CTR 1  having a smaller magnitude than a preset lower bound may be processed by the converter circuit  134 ′, and the second control signal CTR 2  having a magnitude larger than a preset upper bound may be processed by the LED driver  150 . 
     In some embodiments, the converter circuit  134 ′ may further include a dimming off detector. For example, the converter circuit  134 ′ may further include a dimming off detector that performs an operation similar to that of a dimming off detector  151  of  FIG. 11 . An example of the dimming off detector will be described below with reference to FIG. 
       FIG. 8A  is a diagram showing an example of the LED driver  150  of  FIG. 2  according to an example embodiment of the disclosure, and  FIG. 8B  is a diagram showing an example of the operation of the LED driver  150   a  of  FIG. 8A  according to an example embodiment of the disclosure. As shown in  FIG. 8A , the LED driver  150   a  may receive the input voltage V_IN and the second control signal CTR 2  and may provide the LED driving current I_LED to the LED array  160   a.  In some embodiments, the LED driver  150   a  may provide the input voltage V_IN to the LED array  160   a  and may adjust the LED driving current I_LED. 
     The LED array  160   a  may include an LED string STR including a plurality of LEDs connected in series. The LED string STR may include a plurality of LED groups G 1  to G 4 . The LED groups G 1  to G 4  may each include at least one LED, may have a configuration in which a plurality of LEDs are connected in series, and may have a configuration in which a plurality of LEDs are connected in series and in parallel. As shown in  FIG. 8A , coupling points between both ends of the LED string STR and the LED groups G 1  to G 4  may be connected to the LED driver  150   a.    
     The LED driver  150   a  may include a converter  152   a  and a plurality of current sources  153   a  to  156   a.  The converter  152   a  may generate a dimming signal DIM by converting the second control signal CTR 2 . For example, as described above with reference to  FIG. 6 , the second control signal CTR 2  may have a variable current or a variable voltage, and the converter  152   a  may generate the dimming signal DIM having a variable voltage by converting the second control signal CTR 2  or may generate the dimming signal DIM having a variable current according to configurations of the current sources  153   a  to  156   a.  In some embodiments, the converter  152   a  may include a limiter that limits the second control signal CTR 2  to an upper bound and/or a lower bound, similar to the limiter  134 _ 2  of  FIG. 6 . Also, in some embodiments, the converter  152   a  may be omitted when the second control signal CTR 2  converted to a variable voltage corresponds to the range of the dimming signal DIM that is acceptable by the LED driver  150   a.  The dimming signal DIM may be provided to the plurality of current sources  153   a  to  156   a  and may be used to adjust the magnitudes of currents I 1  to I 4  of the plurality of current sources  153   a  to  156   a.    
     The plurality of current sources  153   a  to  156   a  may be connected to connection points between an end of the LED string STR and the LED groups G 1  to G 4 , respectively. As shown in  FIG. 8A , a first current source  153   a  may provide a first current  11  passing through LEDs of the first group G 1 , a second current source  154   a  may provide a second current  12  passing through LEDs of first and second groups G 1  and G 2 , a third current source  155   a  may provide a third current  13  passing through LEDs of first to third groups G 1  to G 3 , and a fourth current source  156   a  may provide a fourth current I 4  passing through LEDs of first to fourth groups G 1  to G 4 . First to fourth currents I 1  to I 4  may be output to the outside of the LED driver  150   a  as the LED driving current I_LED. First to fourth currents sources  153   a  to  156   a  may adjust the currents I 1  to I 4 , respectively, in response to the dimming signal DIM. 
     The LED driver  150   a  of  FIG. 8A  may generate the LED driving current I_LED having a magnitude that follows the magnitude of the full-wave rectified input voltage V_IN. Referring to  FIG. 8B , the first current source  153   a  may be turned on at a time point t 81  from a state in which the first to fourth currents sources  153   a  to  156   a  are turned off, and thus the LED driving current I_LED may have the magnitude of the first current  11 . At a time point t 82 , the first current source  153   a  may be turned off and the second current source  154   a  may be turned on, and thus the LED driving current I_LED may have the magnitude of the second current  12 . In a similar regard, at time points t 83  and t 84 , the third current source  155   a  and the fourth current source  156   a  may be sequentially turned on, and thus the LED driving current I_LED may sequentially have the magnitude of the third current  13  and the magnitude of the fourth current  14 . 
     At a time point t 85 , as the input voltage V_IN decreases, the fourth current source  156   a  may be turned off and the third current source  155   a  may be turned on, and thus the LED driving current I_LED may have the magnitude of the third current  13 . In a similar regard, at time points t 86  and t 87 , the second current source  154   a  and the first current source  153   a  may be sequentially turned on, and thus the LED driving current I_LED may sequentially have the magnitude of the second current  12  and the magnitude of the first current  11 . As such, the method of driving LEDs by generating a current that follows the magnitude of the input voltage V_IN full-wave rectified from the AC voltage V_AC may be referred to as an AC direct LED driving scheme and may provide various advantages by replacing an AC/DC converter for driving LEDs. Korean Patent Publication No. 10-1490332, which is incorporated herein by reference in its entirety and filed by the same applicant as the present application, has proposed the AC direct LED driving method. 
       FIG. 9  is a diagram showing an example of the LED driver  150  of  FIG. 2  according to an example embodiment of the disclosure. Compared with the LED driver  150   a  of  FIG. 8A , a LED driver  150   b  of  FIG. 9  may further include a current supply circuit  158 . Hereinafter, descriptions identical to those of  FIG. 8A  will be omitted. 
     Referring to  FIG. 9 , the LED driver  150   b  may include a converter  152   b,  a plurality of current sources  153   b  to  156   b,  and the current supply circuit  158  and may provide the LED driving current I_LED to a LED array  160   b.  The LED driver  150   b  may adjust the intensity of light emitted by the LED array  160   b  by adjusting the LED driving current I_LED according to the second control signal CTR 2 . When the second control signal CTR 2  corresponding to a low light intensity is received, the magnitude of the LED driving current I_LED may be reduced, and the magnitude of the current I_LED′ transmitted to the power delivery circuit  130  of  FIG. 2  may also be reduced. Accordingly, when the range of light intensity adjustment is large, generation of the positive supply voltage V_DD by the power delivery circuit  130  may not be easy. To resolve this, the LED driver  150   b  may include the current supply circuit  158  as described below. 
     The current supply circuit  158  may receive the dimming signal DIM and generate a supplementary current I_SP. For example, the current supply circuit  158  may recognize the magnitude of the LED driving current I_LED through the dimming signal DIM and, when the recognized magnitude of the LED driving current I_LED is smaller than a preset reference value, the current supply circuit  158  may generate a supplementary current I_SP. In some embodiments, the current supply circuit  158  may generate the supplementary current I_SP of which the magnitude varies according to the dimming signal DIM. Examples of the current supply circuit  158  will be described below with reference to  FIGS. 10A and 10B . As a result, the LED driving current I_LED and the supplementary current I_SP may be provided to the power delivery circuit  130  as the current I_LED′ of  FIG. 2 , and the power delivery circuit  130  may stably generate the positive supply voltage V_DD independently from the light intensity. 
     In some embodiments, the current supply circuit  158  may generate supplementary current I_SP to reduce power consumption and heat generation. For example, the current supply circuit  158  may generate the supplementary current I_SP that is inversely proportional to the input voltage V_IN or generate the supplementary current I_SP that is substantially zero in some intervals of the cycle of the input voltage V_IN. 
       FIGS. 10A and 10B  are circuit diagrams showing examples of the current supply circuit  158  of  FIG. 9  according to example embodiments of the disclosure. As described above with reference to  FIG. 9 , current supply circuits  158   a  and  158   b  of  FIGS. 10A and 10B  may generate the supplementary current I_SP in response to the dimming signal DIM and, as shown in  FIGS. 10A and 10B , may generate the supplementary current I_SP from the input voltage V_IN. 
     Referring to  FIG. 10A , a current supply circuit  158   a  may include operational amplifiers A 11   a , A 12   a,  and A 13   a,  an NMOS transistor N 11   a , and resistors R 11   a  to R 17   a . In  FIG. 10A , voltages V_A, V_SET, DIM, and V_MAX are voltages with respect to a node from which the supplementary current I_SP is output. As shown in  FIG. 10A , a voltage V_A of a source of the NMOS transistor N 11   a  may be calculated as shown in [Equation 2] below. 
     
       
         
           
             
               
                 
                   
                     V_A 
                     = 
                     
                       
                         
                           R 
                            
                           1 
                            
                           5 
                            
                           a 
                         
                         
                           R 
                            
                           1 
                            
                           3 
                            
                           a 
                         
                       
                        
                       
                         ( 
                         
                           
                             V 
                              
                             
                                 
                             
                              
                             SET 
                           
                           - 
                           DIM 
                         
                         ) 
                       
                     
                   
                   , 
                   
                     
 
                   
                    
                   
                     
                       where 
                        
                       
                           
                       
                        
                       R 
                        
                       
                           
                       
                        
                       13 
                        
                       a 
                     
                     = 
                     
                       
                         R 
                          
                         
                             
                         
                          
                         14 
                          
                         a 
                          
                         
                             
                         
                          
                         and 
                          
                         
                             
                         
                          
                         R 
                          
                         
                             
                         
                          
                         15 
                          
                         a 
                       
                       = 
                       
                         R 
                          
                         
                             
                         
                          
                         16 
                          
                         a 
                       
                     
                   
                 
               
               
                 
                   [ 
                   
                     Equation 
                      
                     
                         
                     
                      
                     2 
                   
                   ] 
                 
               
             
           
         
       
     
     When “R 13   a =R 15   a ” in [Equation 2], it is “V_A=V_SET-DIM”, and thus the supplementary current I_SP may be calculated as shown in [Equation 3] below. 
     
       
         
           
             
               
                 
                   I_SP 
                   = 
                   
                     
                       V_SET 
                       - 
                       DIM 
                     
                     
                       R 
                        
                       1 
                        
                       7 
                        
                       a 
                     
                   
                 
               
               
                 
                   [ 
                   
                     Equation 
                      
                     
                         
                     
                      
                     3 
                   
                   ] 
                 
               
             
           
         
       
     
     According to [Equation 3], the magnitude of the supplementary current I_SP is approximately zero when the voltage of the dimming signal DIM exceeds a voltage “V_SET”. When the voltage of the dimming signal DIM is lower than the voltage “V_SET”, the magnitude of the supplementary current I_SP may increase as the voltage of the dimming signal DIM decreases. As shown in  FIG. 10A , the voltage “V_SET” may be determined by a voltage “V_MAX” and resistors R 11   a  and R 12   a.  Meanwhile, operational amplifiers A 11   a  and A 12   a  of the current supply circuit  158   a  of  FIG. 10A  are for eliminating the loading effect of resistors R 13   a  and R 15   a  and resistors R 14   a  and R 16   a,  respectively. In some embodiments, both the operational amplifiers A 11   a  and A 12   a  may be omitted or one the operational amplifier A 11   a  or A 12   a  may be omitted. 
     Referring to  FIG. 10B , the current supply circuit  158   b  may include operational amplifiers A 11   b , A 12   b,  and A 13   b,  NMOS transistors N 11   b , N 12   b,  and N 13   b,  PMOS transistors P 11   b , P 12   b,  P 13   b,  and P 14   b,  and resistors R 11   b  to R 16   b.  In  FIG. 10B , voltages V_B, V_SET, DIM, and V_MAX are voltages with respect to a node from which the supplementary current I_SP is output. As shown in  FIG. 10B , a drain current I_X of an NMOS transistor N 11   b  and a drain current I_Y of an NMOS transistor N 12   b  may be calculated as shown in [Equation 4] below. 
     
       
         
           
             
               
                 
                   
                     I_X 
                     = 
                     
                       DIM 
                       
                         R 
                          
                         1 
                          
                         1 
                          
                         b 
                       
                     
                   
                   , 
                   
                     I_Y 
                     = 
                     
                       V_SET 
                       
                         R 
                          
                         1 
                          
                         4 
                          
                         b 
                       
                     
                   
                 
               
               
                 
                   [ 
                   
                     Equation 
                      
                     
                         
                     
                      
                     4 
                   
                   ] 
                 
               
             
           
         
       
     
     A pair of PMOS transistor P 11   b  and P 12   b  may form a current mirror, and a pair of PMOS transistors P 13   b  and P 14   b  may also form a current mirror. Therefore, a drain current I_Z of a PMOS transistor P 14   b  may correspond to a difference between the drain current I_X and the drain current I_Y, as shown in [Equation 5] below. 
     
       
         
           
             
               
                 
                   I_Z 
                   = 
                   
                     
                       I_Y 
                       - 
                       I_X 
                     
                     = 
                     
                       
                         V_SET 
                         
                           R 
                            
                           1 
                            
                           4 
                            
                           b 
                         
                       
                       - 
                       
                         DIM 
                         
                           R 
                            
                           
                               
                           
                            
                           11 
                            
                           b 
                         
                       
                     
                   
                 
               
               
                 
                   [ 
                   
                     Equation 
                      
                     
                         
                     
                      
                     5 
                   
                   ] 
                 
               
             
           
         
       
     
     Therefore, a source voltage V_B of an NMOS transistor N 13   b  may be calculated as shown in [Equation 6] below. 
     
       
         
           
             
               
                 
                   V_B 
                   = 
                   
                     
                       
                         I_Z 
                         · 
                         R 
                       
                        
                       
                           
                       
                        
                       15 
                        
                       b 
                     
                     = 
                     
                       
                         
                           
                             R 
                              
                             1 
                              
                             5 
                              
                             b 
                           
                           
                             R 
                              
                             1 
                              
                             4 
                              
                             b 
                           
                         
                          
                         V_SET 
                       
                       - 
                       
                         
                           
                             R 
                              
                             1 
                              
                             5 
                              
                             b 
                           
                           
                             R 
                              
                             1 
                              
                             1 
                              
                             b 
                           
                         
                          
                         DIM 
                       
                     
                   
                 
               
               
                 
                   [ 
                   
                     Equation 
                      
                     
                         
                     
                      
                     6 
                   
                   ] 
                 
               
             
           
         
       
     
     When “R 11   b  =R 14   b  =R 15   b ”, it is “V_Z=V_SET-DIM”, and thus the supplementary current I_SP may be calculated as shown in [Equation 7] below. 
     
       
         
           
             
               
                 
                   I_SP 
                   = 
                   
                     
                       V_SET 
                       - 
                       DIM 
                     
                     
                       R 
                        
                       1 
                        
                       6 
                        
                       b 
                     
                   
                 
               
               
                 
                   [ 
                   
                     Equation 
                      
                     
                         
                     
                      
                     7 
                   
                   ] 
                 
               
             
           
         
       
     
     According to [Equation 7], the magnitude of the supplementary current I_SP is approximately zero when the voltage of the dimming signal DIM exceeds the voltage “V_SET”. When the voltage of the dimming signal DIM is lower than the voltage “V_SET”, the magnitude of the supplementary current I_SP may increase as the voltage of the dimming signal DIM decreases. As shown in  FIG. 10B , the voltage “V_SET” may be determined by the voltage “V_MAX” and resistors R 12   b  and R 13   b.    
       FIG. 11  is a block diagram showing an example of the LED driver  150  of  FIG. 2  according to an example embodiment of the disclosure. Compared with the LED driver  150   b  of  FIG. 9 , a LED driver  150   c  of  FIG. 11  may further include a dimming off detector  151  and a dimming off current supply circuit  159 . Hereinafter, descriptions identical to those of  FIG. 8A  and  FIG. 9  will be omitted. 
     Referring to  FIG. 11 , the LED driver  150   c  may include a converter  152   c,  a plurality of current sources  153   c  to  156   c,  a current supply circuit  158   c,  the dimming off detector  151 , and the dimming off current supply circuit  159  and may provide the LED driving current I_LED to a LED array  160   c.  The LED driver  150   c  may adjust the intensity of light emitted by the LED array  160   c  by adjusting the LED driving current I_LED according to the second control signal CTR 2 . In some embodiments, as in the example described above with reference to  FIG. 7B , while the lighting apparatus  100  of  FIG. 2  is being turned off in response to the external signal EXT, which corresponds to the external signal EXT of  FIG. 6  and makes the magnitude of the first control signal CTR 1  smaller than the preset lower bound V_LB, that is, while no light is emitted by the LED array  160   c , power corresponding to a standby state may be supplied to the peripheral component  140 . For example, when the external signal EXT by which the LED array  160   c  may emit light again from a turned off state is input (e.g., when the external signal EXT that makes the first control signal CTR 1  becomes greater than the preset lower bound V_LB is input), only power (e.g., a standby power) for the peripheral component  140  to be in the standby state normally receiving the external signal EXT and providing the first control signal CTR 1  corresponding thereto may be supplied to the peripheral component  140 . 
     As described above, when the dimming signal DIM is input at a level lower than or equal to a preset level, the supplementary current I_SP of the current supply circuit  158   c  may increase as the dimming signal DIM decreases. In some embodiments, similar to the LED driving current I_LED shown in  FIG. 8B , the supplementary current I_SP of the current supply circuit  158   c  may follow the input voltage V_IN, and thus, when dimming off, the power consumption of the current supply circuit  158   c  may be greater than power consumption of the lighting apparatus  100  in the standby state. Therefore, it may be necessary to turn off the current supply circuit  158   c  to reduce power consumption in a dimming off state, that is, the standby state. In the dimming off state, when the current I_LED is approximately zero and the supplementary current I_SP is also approximately zero as the current supply circuit  158   c  is turned off, the current I_LED′ of the lighting apparatus  100  of  FIG. 2  may become approximately zero, and thus it may not be easy for the power delivery circuit  130  to supply power to the peripheral component  140 . 
     In the dimming off state, the dimming off current supply circuit  159  may provide an OFF current I_OFF for reducing power consumption of the lighting apparatus  100  and supplying the standby power to the peripheral component  140 . The dimming off detector  151  may detect the dimming off state from the dimming signal DIM and output a dimming off signal DIM_OFF according to the detected dimming off state. In some embodiments, the dimming off detector  151  may receive the second control signal CTR 2  and may output the dimming off signal DIM_OFF according to the second control signal CTR 2 . In some embodiments, the dimming off detector  151  may receive a separate signal indicating the dimming off state, e.g., a dimming off control signal, from the power delivery circuit  130  and output the dimming off signal DIM_OFF according to the dimming off control signal. When the dimming off signal DIM_OFF is activated, the current supply circuit  158   c  is turned off, and thus the supplementary current I_SP may become approximately zero. Meanwhile, the dimming off current supply circuit  159  may be turned on and supply the OFF current I_OFF to the power delivery circuit  130  of the lighting apparatus  100 . 
     As described above, the LED driver  150   c  may include the dimming off detector  151  and the dimming off current supply circuit  159  to supply the standby power to the peripheral component  140  when the lighting apparatus  100  is in the standby state. However, as exemplified with reference to  FIG. 12 , it will be understood that various methods may be employed to supply standby power to the peripheral components  140  when the lighting apparatus  100  of  FIG. 2  is in the dimming off state according to example embodiments of the disclosure. 
       FIG. 12  is a block diagram showing an example of the power delivery circuit  130  of  FIG. 2  according to an example embodiment of the disclosure. In detail,  FIG. 12  shows a power delivery circuit  130 ″ supplying standby power to the peripheral component  140  when the lighting apparatus  100  in the dimming off state. As shown in  FIG. 12 , the power delivery circuit  130 ″ may include a dimming off detector  131  and a dimming off current supply circuit  139  similar to the dimming off detector  151  and the dimming off current supply circuit  159  included in the LED driver  150   c  of  FIG. 11 . Hereinafter, it is assumed that the power delivery circuit  130 ″ of  FIG. 12  receives a current supplied from the LED driver  150   b  of  FIG. 9 , and  FIG. 12  will be described with reference to  FIG. 9 . Also, descriptions identical to those of  FIG. 3  will be omitted. 
     Referring to  FIG. 12 , the power delivery circuit  130 ″ may further include a regulator circuit  132 ′, a converter circuit  134 ′, the dimming off detector  131 , and the dimming off current supply circuit  139 . The regulator circuit  132 ′ may receive the LED driving current I_LED and the supplementary current I_SP from the LED driver  150   b  of  FIG. 9  and may additionally receive the OFF current I_OFF from the dimming off current supply circuit  139  in the power delivery circuit  130 ″. As shown in  FIG. 12 , compared to the power delivery circuit  130 ′ of  FIG. 3 , the power delivery circuit  130 ″ may receive the input voltage V_IN to supply power to the dimming off current supply circuit  139 . 
     When the lighting apparatus  100  of  FIG. 2  enters the standby state by receiving the external signal EXT that makes the magnitude of the first control signal CTR 1  of  FIG. 6  to become smaller than the preset lower bound V_UB, the LED driver  150   b  may provide the LED driving current I_LED and the supplementary current I_SP that are approximately zero (due to, for example, a dimming off detector similar to the dimming off detector  151  exemplified in  FIG. 11 ). In some embodiments, the dimming off signal DIM_OFF of the dimming off detector  131  included in the power delivery circuit  130 ″ of  FIG. 12  may be provided to the LED driver  150   b  of  FIG. 9 , and the LED driver  150   b  of  FIG. 9  may provide the LED driving current I_LED and the supplementary current I_SP, which are approximately zero, in response to the dimming off signal DIM_OFF. 
     When the lighting apparatus  100  of  FIG. 2  enters the standby state, the dimming off detector  131  may detect the dimming off state from the second control signal CTR 2  and output the dimming off signal DIM_OFF. In some embodiments, the dimming off detector  131  may receive a first control signal CTR 1  and may output the dimming off signal DIM_OFF based on the first control signal CTR 1 . When the dimming off signal DIM_OFF is activated, the dimming off current supply circuit  139  may be turned on and supply the OFF current I_OFF to the regulator circuit  132 ′ of the power delivery circuit  130 ″. In some embodiments, a portion of regulator circuit  132 , e.g., the shunt regulator  132 _ 2  of  FIG. 4 , may be turned off according to the activated dimming off signal DIM_OFF. 
     In some embodiments, when the lighting apparatus  100  of  FIG. 2  enters the standby state, a shunt regulator (e.g.,  132 _ 2  of  FIG. 4 ) included in the regulator circuit  132 ′ may be turned off when the dimming off signal DIM_OFF is activated. As described above with reference to  FIGS. 5A to 5C , the shunt regulator included in the regulator circuit  132 ′ may receive the current I_LED′ and regulate the first positive supply voltage V_DD 1 . Therefore, controlling the average current of the OFF current I_OFF of the dimming off current supply circuit  139  to entirely become a supply current needed in the standby state, instead of providing an average current of the OFF current I_OFF of the dimming off current supply circuit  139  to the shunt regulator of the regulator circuit  132 ′, may be more efficient to reduce the power consumption of the lighting apparatus  100  in the standby state. Similarly, it may be more efficient that the average current of the OFF current I_OFF of the dimming off current supply circuit  159  of  FIG. 11  entirely becomes the supply current needed in the standby state of the peripheral components  140 . Hereinafter, examples of controlling the regulator circuit  132 ′ in the dimming off state will be described below with reference to  FIGS. 13A to 13C , and examples of the dimming off current supply circuits  139  and  159  of  FIGS. 11 and 12  will be described below with reference to  FIGS. 14A to 14C . 
       FIGS. 13A to 13C  are circuit diagrams showing examples of the shunt regulator  132 _ 2  of  FIG. 4  according to example embodiments of the disclosure. In detail, shunt regulators of  FIGS. 13A to 13C  may receive the dimming off signal DIM_OFF as compared to shunt regulators  132 _ 2   a,    132 _ 2   b,  and  132 _ 2   c  of  FIGS. 5A through 5C . Hereinafter, descriptions identical to those of  FIG. 5A  and  FIG. 5C  will be omitted. 
     Referring to  FIG. 13A , in a shunt regulator  132 _ 2   a ′, according to the activated (that is, high level) dimming off signal DIM_OFF, an output G 1  of an inverter INV may be at a low level, and an NMOS transistor N 53  may be turned off. Therefore, a current passing through a zener diode Z 51  may be blocked, and thus the shunt regulator  132 _ 2   a ′ may be turned off. Referring to  FIG. 13B , in a shunt regulator  132 _ 2   b ′, according to the activated dimming off signal DIM_OFF, an NMOS transistor N 53  may be turned on, and thus the NMOS transistor N 51  may be turned off. As a result, the shunt regulator  132 _ 2   b ′ may be turned off. Referring to  FIG. 13C , in a shunt regulator  132 _ 2   c ′, according to the activated dimming off signal DIM_OFF, an NMOS transistor N 53  may be turned on, and thus a PMOS transistor P 51  may be turned off. As a result, the shunt regulator  132 _ 2   c ′ may be turned off. Shunt regulators  132 _ 2   a ′,  132 _ 2   b ′, and  132 _ 2   c ′ described above with reference to  FIGS. 13A to 13C  are merely examples, and it will be understood that various types of shunt regulators that are turned off in response to the dimming off signal DIM_OFF may be employed according to example embodiments of the disclosure. 
       FIGS. 14A to 14C  are diagrams showing examples of reducing power consumption of the lighting apparatus  100  of the  FIG. 2  in the standby state according to example embodiments of the disclosure. In detail,  FIG. 14A  is a graph showing examples of operation intervals of the dimming off current supply circuits  139  and  159  and waveforms of the OFF current I_OFF of the dimming off current supply circuits  139  and  159  of  FIGS. 11 and 12 , and  FIGS. 14B and 14C  are block diagrams showing respective examples  139 ′ and  159 ′ of the dimming off current supply circuits  139  and  159  of  FIGS. 11 and 12  according to example embodiments of the disclosure. Hereinafter,  FIGS. 14A to 14C  will be described with reference to the dimming off current supply circuit  139  of  FIG. 12 , but it will be understood that the same or similar descriptions may be applied to the dimming off current supply circuit  159  of  FIG. 11 . Hereinafter, redundant descriptions of  FIGS. 14B and 14C  will be omitted. 
     Referring to  FIG. 14A , when the dimming off signal DIM_OFF is activated, to reduce power consumption of the lighting apparatus  100  in the standby state, the dimming off current supply circuit  139  of  FIG. 12  may supply the OFF current I_OFF by being activated in an interval (e.g., an interval from a time point T 91  to a time point t 94 ) in which the input voltage V_IN is smaller than a voltage VIN_H at every cycle of the input voltage V_IN. In addition, in an interval in which the input voltage V_IN is greater than a voltage VIN_L but smaller than the voltage VIN _H (e.g., an interval between the time point t 91  and a time point t 92  and an interval between a time point t 93  and the time point t 94 ), the dimming off current supply circuit  139  may supply a maximum OFF current (IOFFmax). In an interval in which the input voltage V_IN is less than the voltage VIN_L (e.g., an interval between the time point t 92  and the time point t 93 ), the dimming off current supply circuit  139  may supply the OFF current I_OFF that decreases as the input voltage V_IN decreases. 
     For the average current of the OFF current I_OFF of the dimming off current supply circuit  139  to become a current demanded by the peripheral component  140  in the standby state, in some embodiments, the magnitude of the maximum OFF current IOFFmax may be controlled while a current supplying interval (e.g., the interval between the time point t 91  and the time point t 94 ) is fixed. In some other embodiments, the magnitude of the voltage VIN_H may be controlled while the maximum OFF current IOFFmax is fixed, thereby extending or shortening the current supplying interval (e.g., the interval between the time point t 91  and the time point t 94 ). 
     Referring to  FIG. 14B , the average current of the OFF current I_OFF generated by the dimming off current supply circuit  139 ′ may be controlled to be the current demanded by the peripheral component  140  in the standby state by controlling the magnitude of the maximum OFF current IOFFmax. As shown in  FIG. 14B , the dimming off current supply circuit  139 ′ may include an input voltage level detector  139 _ 1 , an error amplifier  139 _ 2 , a level shifter  139 _ 3 , an OFF reference circuit  139 _ 4 , logic gates INV and OR, an operational amplifier A 22 , NMOS transistors N 22  and N 24 , and resistors R 22  to R 24 . An output SIG 2  of the inverter INV may be at a high level and an output SIG 3  of an OR_gate OR may be at a high level according to the dimming off signal DIM_OFF which is deactivated, that is, at a low level. Therefore, An NMOS transistor N 24  may be turned on and an NMOS transistor N 22  may be turned off, and thus the OFF current I_OFF may be approximately zero. On the other hand, according to the activated (that is, at the high level) dimming off signal (DIM_OFF), the output SIG 2  of the inverter INV may be at the low level, and the output SIG 3  of the OR_gate OR may be at the high level or the low level according to an output SIG 1  of the input voltage level detector  139 _ 1 , and thus the NMOS transistor N 22  may be in the ON state, that is, a state for supplying the OFF current I_OFF or in the OFF state. 
     When the dimming off signal DIM_OFF is activated and the input voltage V_IN greater than a preset voltage VIN_H is input to the input voltage level detector  139 _ 1 , the output SIG 1  may be at the high level. Therefore, the NMOS transistor N 22  may be turned off, and thus the OFF current I_OFF may be approximately zero. On the other hand, when the input voltage V_IN smaller than the preset voltage VIN_H is input to the input voltage level detector  139 _ 1 , both outputs SIG 1  and SIG 3  may be at the low level, and thus the NMOS transistor N 24  may be turned off. Therefore, the dimming off current supply circuit  139 ′ may operate normally and supply the OFF current I_OFF to a node of the first positive supply voltage V_DD 1 . 
     The error amplifier  139 _ 2  may generate a voltage Ve by comparing a reference voltage VREF with a voltage VDIV divided by the resistors R 23  and R 24  and amplifying an error therebetween and output the voltage Ve to the level shifter  139 _ 3 . The OFF reference circuit  139 _ 4  may receive an output voltage Ve′ of the level shifter  139 _ 3  and output a voltage VREF_OFF that is generated with respect to the first positive supply voltage V_DD 1 . An output voltage Ve of the error amplifier  139 _ 2  is generated with respect to a ground voltage, whereas an output voltage VREF_OFF of the OFF reference circuit  139 _ 4  is generated with respect to the first positive supply voltage V_DD 1 . 
     Therefore, DC level shifting of the output voltage Ve of the error amplifier  139 _ 2  may be necessary, such that the output voltage VREF_OFF of the OFF reference circuit  139 _ 4  increases or decreases with respect to the first positive supply voltage V_DD 1  as the output voltage Ve increases or decreases. The level shifter  139 _ 3  may provide such a DC level shifting, output a DC level shifted voltage Ve′ from the output voltage Ve of the error amplifier  139 _ 2 , and supply the DC level shifted voltage Ve′ to the OFF reference circuit  139 _ 4 . 
     In the example of  FIG. 14B , when the first positive supply voltage V_DD 1  gradually increases/decreases, the voltages VDIV divided by the resistors R 23  and R 24  may also gradually increase/decrease. Therefore, the error amplifier  139 _ 2  may compare the reference voltage VREF with the divided voltage VDIV, amplify an error therebetween, and output the voltage Ve gradually decreasing/increasing, and the output voltage Ve′ of the level shifter  139 _ 3  may also gradually decrease/increase. As the output voltage Ve′ of the level shifter  139 _ 3  gradually decreases/increases, the output voltage VREF_OFF of the OFF reference circuit  139 _ 4  may gradually decrease/increase, and the maximum OFF current IOFFmax of the dimming off current supply circuit  139 ′ may also gradually decrease/increase, and thus a feedback (i.e., negative feedback) control that offsets increase/decrease of the initial first positive supply voltage V_DD 1  may be provided. According to such a feedback control, the OFF current supply circuit  139 ′ may supply a standby state current for the peripheral component  140  and reduce power consumption of the lighting apparatus  100  of  FIG. 2 . 
     The maximum OFF current IOFFmax of the dimming off current supply circuit  139 ′ may be calculated as shown in [Equation 8] below. 
     
       
         
           
             
               
                 
                   IOFFmax 
                   = 
                   
                     VREF_OFF 
                     
                       R 
                        
                       2 
                        
                       2 
                     
                   
                 
               
               
                 
                   [ 
                   
                     Equation 
                      
                     
                         
                     
                      
                     8 
                   
                   ] 
                 
               
             
           
         
       
     
     Also, the first positive supply voltage V_DD 1  by the dimming off current supply circuit  139 ′ may be calculated as shown in [Equation 9] below. 
     
       
         
           
             
               
                 
                   
                     V_DD 
                      
                     
                         
                     
                      
                     1 
                   
                   = 
                   
                     
                       ( 
                       
                         1 
                         + 
                         
                           
                             R 
                              
                             2 
                              
                             4 
                           
                           
                             R 
                              
                             2 
                              
                             3 
                           
                         
                       
                       ) 
                     
                     · 
                     VREF 
                   
                 
               
               
                 
                   [ 
                   
                     Equation 
                      
                     
                         
                     
                      
                     9 
                   
                   ] 
                 
               
             
           
         
       
     
     Referring to  FIG. 14C , while the maximum OFF current IOFFmax is being fixed, the magnitude of the voltage VIN_H may be controlled to extend or shorten the current supplying interval (e.g., the interval between the time point t 91  and the time point t 94  of  FIG. 14A ), and thus the average voltage of the OFF current I_OFF of a dimming off current supply circuit  139 ″ may be controlled to become a current demanded by the peripheral component  140  in the standby state. As shown in  FIG. 14C , the dimming off current supply circuit  139 ″ may include an input voltage level detector  139 _ 1 ′, an error amplifier  139 _ 2 ′, an OFF reference circuit  139 _ 4 ′, the logic gates INV and OR, an operational amplifier A 22 , the NMOS transistors N 22  and N 24 , and resistors R 22  to R 26 . 
     The input voltage level detector  139 _ 1 ′ may include resistors R 25  and R 26 , a subtractor SUB, and a comparator COMP. The divided voltage VIN_DIV may be generated by dividing the input voltage V_IN by the resistors R 25  and R 26 . The subtractor SUB may supply an output voltage VIN_H′ to the comparator COMP by subtracting a divided voltage VIN_DIV from the output voltage Ve of the error amplifier  139 _ 2 ′, and the comparator COMP may generate the output voltage SIG 1  by comparing the output voltage VIN_H′ of the subtractor SUB with a reference voltage VCMP_R. When the output voltage Ve of the error amplifier  139 _ 2 ′ increases and decreases, the output voltage VIN_H′ may also increase or decrease. Therefore, the current supplying interval (e.g., the interval between the time point t 91  and the time point t 94  of  FIG. 14A ) of the OFF current I_OFF of the dimming off current supply circuit  139 ″ may be extended/shortened. 
     An output SIG 2  of the inverter INV may be at a high level and an output SIG 3  of an OR_gate OR may be at a high level according to the dimming off signal DIM_OFF which is deactivated, that is, at a low level. The NMOS transistor N 24  may be turned on and the NMOS transistor N 22  may be turned off, and thus the OFF current I_OFF may be approximately zero. On the other hand, according to the activated (that is, at the high level) dimming off signal (DIM_OFF), the output SIG 2  of the inverter INV may be at the low level, and the output SIG 3  of the OR_gate OR may be at the high level or the low level according to an output SIG 1  of the input voltage level detector  139 _ 1 ′, and thus the NMOS transistor N 22  may be in the ON state, that is, a state for supplying the OFF current I OFF or in the OFF state. 
     While the dimming off signal DIM_OFF is being enabled, when the output voltage VIN_H′ of the subtractor SUB becomes higher than the reference voltage VCMP_R of the comparator COMP, the output SIG 1  may be at the high level, and thus the NMOS transistor N 22  may be turned off and the OFF current I_OFF may become approximately zero. On the other hand, while the dimming off signal DIM_OFF is being enabled, when the output voltage VIN_H′ of the subtractor SUB becomes lower than the reference voltage VCMP_R of the comparator COMP, the output SIG 1  may be at the low level, and thus the NMOS transistor N 24  may be turned off. Therefore, the dimming off current supply circuit  139 ″ may operate normally and supply the OFF current I_OFF to a node of the first positive supply voltage V_DD 1 . The error amplifier  139 _ 2 ′ may compare the reference voltage VREF with the voltages VDIV divided by resistors R 23  and R 24  and amplify an error therebetween, thereby outputting the voltage Ve to the subtractor SUB of the input voltage level detector  139 _ 1 ′. The OFF reference circuit  139 _ 4 ′ may output a constant voltage VREF_OFF generated with respect to the first positive supply voltage V_DD 1 . Therefore, the maximum OFF current IOFFmax may have a constant value calculated as in [Equation 8] above. 
     In the example of  FIG. 14C , when the first positive supply voltage V_DD 1  gradually increases/decreases, the voltages VDIV divided by the resistors R 23  and R 24  may also gradually increase/decrease. Therefore, the error amplifier  139 _ 2  may compare the reference voltage VREF with the divided voltage VDIV and amplify an error therebetween, thereby outputting the error voltage Ve gradually decreasing/increasing. As the error voltage Ve gradually decreases/increases, the output voltage VIN_H′ of the subtractor SUB may also gradually decrease/increase. Therefore, the current supplying interval (e.g., the interval between the time point t 91  and the time point t 94  of  FIG. 14A ) of the OFF current I_OFF of the dimming off current supply circuit  139 ″ may be shortened/extended. This shortening/extension of the current supplying interval may provide feedback (i.e., negative feedback) control that offsets increase/decrease of the initial first positive supply voltage V_DD 1 . According to such a feedback control, the OFF current supply circuit  139 ″ may supply a standby state current for the peripheral component  140  and reduce power consumption of the lighting apparatus  100  of  FIG. 2 . 
       FIG. 15A  is a diagram showing an example of the LED driver  150  of  FIG. 2  according to an example embodiment of the disclosure, and  FIG. 15B  is a diagram showing an example of a current supply circuit  158   d  of  FIG. 15A  according to an example embodiment of the disclosure. In detail, compared to the LED driver  150   b  of  FIG. 9 , the LED driver  150   d  of  FIG. 15A  may further include an operation interval selection circuit  151   d,  and the current supply circuit  158   d  may receive an operation interval signal OP_INT from the operation interval selection circuit  151   d.  Hereinafter, descriptions identical to those of  FIG. 8A  and  FIG. 9  will be omitted. 
     Referring to  FIG. 15A , the LED driver  150   d  may include a converter  152   d,  the operation interval selection circuit  151   d,  a plurality of current sources  153   d  to  156   d,  and a current supply circuit  158   d  and may provide the LED driving current I_LED to an LED array  160   d.  The operation interval selection circuit  151   d  may receive the dimming signal DIM and an operation interval control signal OP_INT_CTR. The operation interval control signal OP_INT_CTR may indicate an operation interval of the input voltage V_IN in which power consumption in the current supply circuit  158   d  may be lowered. For example, the operation interval control signal OP_INT_CTR may be activated in an interval in which a first current source  153   d  operates (e.g., an interval between a time point t 81  and a time point t 82  and an interval between a time point t 87  and a time point t 88  in  FIG. 8B ), an interval in which the first current source  153   d  and a second current source  154   d  operate (e.g., an interval between the time point t 81  and a time point t 83  and an interval between a time point t 86  and the time point t 88  in  FIG. 8B ), or an interval in which first to fourth current sources  153   d  to  156   d  are all deactivated (e.g., an interval before the time point t 81  and an interval after the time point t 88  in  FIG. 8B ), from among intervals in which the first to fourth current sources  153   d  to  156   d  operate. In some embodiments, the operation interval control signal OP_INT_CTR may be activated based on time points at which the first to fourth currents source  153   d  to  156   d  are turned on or turned off or may be activated based on the magnitude of the input voltage V_IN. 
     In some embodiments, when the operation interval control signal OP_INT_CTR is activated and the dimming signal DIM corresponding to the LED driving current I_LED lower than a preset reference value is received, the operation interval signal OP_INT may be activated (e.g., high level). The current supply circuit  158   d  may provide the supplementary current I_SP only during intervals in which the input voltage V_IN is relatively low in response to the activated operation interval signal OP_INT. Therefore, power consumption of the current supply circuit  158   d  may be reduced, and power consumption and heat generation of the LED driver  150   d  may be reduced. In this case, the supplementary current I_SP of the current supply circuit  158   d  may depend on the dimming signal DIM, for example, as described above with reference to  FIGS. 10A and 10B , may follow the input voltage V_IN, may be a current inversely proportional to the input voltage V_IN, may have an arbitrary current waveform, or may have a constant magnitude independent of the dimming signal DIM. 
     Referring to  FIG. 15B , compared with the current supply circuit  158   a  of  FIG. 10A , a current supply circuit  158   d ′ of  FIG. 15B  may further include an NMOS transistor N 12   d  and the inverter INV and may further receive the operation interval signal OP_INT. Hereinafter, descriptions identical to those of  FIG. 10A  will be omitted. When the activated (e.g., high level) operation interval signal OP_INT is received, the NMOS transistor N 12   d  may be turned off, and thus the current supply circuit  158   d ′ may supply the supplementary current I_SP as shown in [Equation 3]. On the other hand, when a deactivated (e.g., low level) operation interval signal OP_INT is received, the NMOS transistor N 12   d  may be turned on and an NMOS transistor N 11   d  may be turned off, and thus the supplementary current I_SP may be approximately zero. 
     In some embodiments, the current supply circuit  158   d ′ of  FIG. 15B  may be implemented within the power delivery circuit  130  of  FIG. 2 . For example, the dimming off current supply circuit  139  of  FIG. 12  may receive the operation interval signal OP_INT and perform the same or similar function as that of the current supply circuit  158   d  described above with reference to  FIG. 15B . Also, in some embodiments, the current supply circuit  158   d  of  FIG. 15A  may supply the supplementary current I_SP only during intervals in which the operation interval signal OP_INT is activated. 
       FIG. 16A  is a diagram showing an example of the power delivery circuit  130  of  FIG. 2  according to an example embodiment of the disclosure, and  FIG. 16B  is a diagram showing an example of a dimming off current supply circuit  139 ′″ of  FIG. 16A  according to an example embodiment of the disclosure. In detail, a power delivery circuit  130 ′″ of  FIG. 16A  includes the dimming off current supply circuit  139 ′ that provides a current to a regulator circuit  132 ″ not only in the dimming off state, but also in a state in which the LED driving current I_LED is insufficient due to dimming control. Compared with the power delivery circuit  130 ″ of  FIG. 12 , the power delivery circuit  130 ′″ of  FIG. 16A  may further include a dimming level detector  135  and may receive only the LED driving current I_LED (for example, from the LED driver  150   a  of  FIG. 8A ) based on the dimming level detector  135  and the dimming off current supply circuit  139 ′. In some embodiments, the dimming level detector  135  may be included in the dimming off current supply circuit  139 ′″. Hereinafter, it is assumed that the power delivery circuit  130 ′″ of  FIG. 16A  receives the current I_LED from the LED driver  150   a  of  FIG. 8A , and descriptions identical to those of  FIG. 12  will be omitted. 
     Referring to  FIG. 16A , the power delivery circuit  130 ′″ may include the regulator circuit  132 ″, a converter circuit  134 ″, a dimming off detector  131 ′, the dimming off current supply circuit  139 ′″, and the dimming level detector  135 . The dimming off current supply circuit  139 ′″ may not receive the dimming off signal DIM_OFF, and thus the OFF current I _OFF may be supplied to the regulator circuit  132 ″ regardless of whether the dimming off signal DIM_OFF is activated. 
     The dimming off current supply circuit  139 ′″ may provide a current corresponding to the supplementary current I_SP, as described below with reference to  FIGS. 17A to 17C . The dimming level detector  135  may receive the second control signal CTR 2  from the converter circuit  134 ″ and generate a dimming level signal DIM_LVL, and the dimming off current supply circuit  139 ′ may receive the dimming level signal DIM_LVL may be received from the dimming level detector  135 . In some embodiments, the dimming level detector  135  may receive the first control signal CTR 1  and generate the dimming level signal DIM_LVL. When the second control signal CTR 2  corresponds to a dimming level below a pre-defined dimming level, the dimming level detector  135  may provide an activated (e.g., high level) dimming level signal DIM_LVL to the dimming off current supply circuit  139 ′″. Otherwise, the dimming level detector  135  may provide a deactivated (e.g., low level) dimming level signal DIM_LVL to the dimming off current supply circuit  139 ′″. 
     Referring to  FIG. 16B , when compared to the dimming off current supply circuit  139 ′ of  FIG. 14B , the dimming off current supply circuit  139 ′″ of  FIG. 16B  may receive the dimming level signal DIM_LVL instead of the dimming off signal DIM_OFF and may include the same components as those of the dimming off current supply circuit  139 ′ of  FIG. 14B , wherein the like reference numerals denote the like elements for convenience of explanation. Hereinafter, descriptions identical to those of  FIG. 14B  will be omitted. 
     When a dimming level corresponding to the second control signal CTR 2  is equal to or higher than a pre-defined dimming level (e.g., 90%), the dimming level detector  135  may provide a deactivated (e.g., low level) dimming level signal DIM_LVL. Therefore, by the turned-on NMOS transistor N 24  and the turned-off NMOS transistor N 22 , the OFF current I_OFF may become approximately zero. On the other hand, when a dimming level corresponding to the second control signal CTR 2  is lower than or equal to the pre-defined dimming level (e.g., 90%), the dimming level detector  135  may provide an activated (e.g., high level) dimming level signal DIM_LVL. Therefore, the OFF current I_OFF may be supplied to a node of the first positive supply voltage V_DD 1  node according to the output SIG 1  of the input voltage level detector  139 _ 1 . 
     In the negative feedback control system of  FIG. 16B , the error amplifier  139 _ 2  may output the output voltage Ve that is (e.g., linearly) proportional to a difference between two inputs VREF and VDIV. For example, the output voltage Ve may increase when the divided voltage VDIV is lower than the reference voltage VREF and may decrease when the divided voltage VDIV is higher than the reference voltage VREF. Under a full dimming (e.g., 100% dimming) condition that allow the LED driving current I _LED to be supplied at its maximum value, the first positive supply voltage V_DD 1  may have a maximum value, and thus the output voltage Ve of the error amplifier  139 _ 2  may be a minimum voltage Ve_min. In some embodiments, even when the output voltage Ve of the error amplifier  139 _ 2  is the minimum output voltage Ve_min, a non-zero OFF current I_OFF may be generated. 
     As described above, the OFF current I_OFF may have a pulse waveform, thereby deteriorating characteristics such as electromagnetic interference (EMI). In some embodiments, even under such a full dimming condition, for a lighting apparatus (e.g.,  100  of  FIG. 2 ) to have excellent characteristics, the dimming off current supply circuit  139 ′″ may receive the dimming level signal DIM_LVL that is deactivated (i.e., low level) when the dimming level is equal to or higher than a preset dimming level (e.g., 90%) and, as the NMOS transistor N 22  of  FIG. 16B  is turned off, the OFF current I_OFF may become approximately zero. In some embodiments, under a full dimming condition in which the output voltage Ve of the error amplifier  139 _ 2  becomes the minimum voltage Ve_min according to the circuit configuration of  FIG. 16B , the dimming off current supply circuit  139 ′″ of  FIG. 16B  may provide the OFF current I_OFF that is approximately zero, the dimming level detector  135  may be omitted, and the dimming level signal DIM_LVL may always maintain an activated state (e.g., high level). 
     As described above with reference to  FIG. 4 , the shunt regulator  132 _ 2  of  FIG. 4  needs to receive a current I_LED′ greater than a load current (e.g., I_LOAD of  FIG. 5A ) to maintain the first positive supply voltage V_DD 1  of a certain magnitude V_DD 1 _NOM. In an interval in which the LED driving current I_LED decreases (e.g., an interval in which the LED driving current I_LED following the input voltage V_IN as shown in  FIG. 8B  is approximately zero or the LED driving current I_LED is decreased due to the dimming signal DIM of  FIG. 8A ), capacitors (e.g., C 51   a,  C 51   b,  and C 51   c  of  FIGS. 5A to 5C ) connected to a node from which the first positive supply voltage V_DD 1  is output may supply a current to a load of the first positive supply voltage V_DD 1 . When the average current of the LED driving current I_LED is sufficiently greater than a current provided to the load of the first positive supply voltage V_DD 1  and a capacitor value thereof is also sufficiently large, the first positive supply voltage V_DD 1  supplied by the regulator circuit  132 ′ may be maintained at the constant magnitude V_DD 1 _NOM. 
     When the magnitude of the LED driving current I_LED decreases due to the dimming signal DIM, an interval during which a capacitor supplies a current may be extended, and thus a voltage drop may occur at the first positive supply voltage V_DD 1 . When the dimming level is very low (e.g., 20%), the voltage drop of the first positive supply voltage V_DD 1  may be more significant, and, as shown in  FIG. 4 , the first positive supply voltage V_DD 1  may become a voltage lower than a voltage at which linear regulators  132 _ 6  and  132 _ 8  are capable of normally supplying second and third positive supply voltages V_DD 2  and V_DD 3 . To resolve the problem, as described above with reference to  FIG. 9 , the current supply circuit  158  of  FIG. 9  may provide the supplementary current I _SP. Meanwhile, the power delivery circuit  130 ′″ of  FIG. 16A  may perform a function similar to that of the current supply circuit  158  of  FIG. 9  when the dimming off signal DIM OFF is deactivated, as described below with reference to  FIGS. 17A to 17C . 
       FIGS. 17A to 17C  are diagrams showing examples of the operations of the power delivery circuit  130 ′″ of  FIG. 16A  and the dimming off current supply circuit  139 ′″ of  FIG. 16B , according to example embodiments of the disclosure. In detail,  FIGS. 17A to 17C  show operations of the power delivery circuit  130 ′″ and the dimming off current supply circuit  139 ′″ according to dimming levels. For convenience of explanation, it is assumed that the OFF current I_OFF has a constant magnitude in an interval in which the input voltage V_IN is smaller than a preset voltage (e.g., VIN_H), unlike the waveform shown in  FIG. 14A . Hereinafter,  FIGS. 17A to 17C  will be described with reference to  FIGS. 16A and 16B . 
     Referring to  FIG. 17A , when the dimming off signal DIM_OFF is activated, the LED driving current I_LED, which is approximately zero, may be supplied from an LED driver (e.g.,  150   a  of  FIG. 8A ), and a shunt regulator (e.g.,  132 _ 2  of  FIG. 4 ) of the regulator circuit  132 ″ may be turned off. As shown in  FIG. 17A , due to the OFF current I_OFF having a pulse waveform, the first positive supply voltage V_DD 1  may increase during an interval at which the OFF current I_OFF is supplied and decrease during an interval in which the OFF current I_OFF is approximately zero. In this case, an average value V_DD 1  _REG of the first positive supply voltage V_DD 1  may be calculated as shown in [Equation 9] through a negative feedback control of the dimming off current supply circuit  139 ′″ of  FIG. 16B . Meanwhile, the maximum value I_OFF_MAX of the OFF current I_OFF may be determined through a feedback control, such that an average value of the OFF current I_OFF coincides with a current provided to the load of the first positive supply voltage V_DD 1 . The capacitance of the capacitor C 51  may be determined to be equal to or greater than a capacitance for normally operating linear regulators (e.g.,  132 _ 6  and  132 _ 8  of  FIG. 4 ) of the regulator circuit  132 ″ even when the first positive supply voltage V_DD 1  becomes minimum. 
     Referring to  FIG. 17B , when the dimming off signal DIM_OFF is deactivated but, due to a low dimming level (e.g., 30%), an average value of the LED driving current I_LED is smaller than a current provided to the load of the first positive supply voltage V_DD 1 , the dimming off current supply circuit  139 ′″ may perform a feedback control, such that a sum of the average I_OFF_AVG of the OFF current I_OFF and an average I_LED_AVG of the current I_LED of the LED driver coincides with the current provided to the load of the first positive supply voltage V_DD 1 . In other words, a maximum value I_OFF_M of the OFF current I_OFF may be determined as a value, such that “I_OFF_AVG+I_LED AVG” coincides with the current provided to the load of the first positive supply voltage V_DD 1 . 
     Referring to  FIG. 17C , when the dimming level is equal to or higher than a pre-defined dimming level (e.g., 90%), according to a deactivated (i.e., low level) dimming level signal DIM_LVL, the NMOS transistor N 22  may be turned off, and the OFF current I_OFF may be approximately zero. However, due to a very high dimming level, an average current of the current I_LED received from an LED driver (e.g.,  150   a  of  FIG. 8A ) may be much greater than a load current I_LOAD, and thus a shunt regulator (e.g.,  132 _ 2  of  FIG. 4 ) of the regulator circuit  132 ″ of  FIG. 16A  may operate normally, and the first positive supply voltage V_DD 1  may maintain the constant magnitude V_DD 1 _NOM. 
       FIGS. 18A and 18B  are block diagrams showing examples of a lighting apparatus according to example embodiments of the disclosure. In detail,  FIGS. 18A and 18B  show example lighting apparatuses  200  and  300  each including a plurality of LED sub-arrays including LEDs having different color temperatures. Hereinafter, redundant descriptions of  FIGS. 18A and 18B  will be omitted. 
     Referring to  FIG. 18A , a lighting apparatus  200  may receive the AC voltage V_AC and may include a full-wave rectifier  202 , first and second power delivery circuits  213  and  223 , a peripheral component  214 , first and second LED driver  215  and  225 , and first and second LED sub-arrays  216  and  226 . The first and second LED sub-arrays  216  and  226  may each include LEDs having different color temperatures. For example, a first LED sub-array  216  may include LEDs having a color temperature of about 2500K, whereas a second LED sub-array  226  may include LEDs having a color temperature of about 6500K. The lighting apparatus  200  may adjust a first LED driving current I_LED 1  provided to the first LED sub-array  216  and a second LED driving current I_LED 2  provided to the second LED sub-array  226 , thereby controlling the color temperature of light emitted by the lighting apparatus  200 . 
     As shown in  FIG. 18A , to adjust the first LED driving current I_LED 1  and the second LED driving current I_LED 2  provided to the first LED sub-array  216  and the second LED sub-array  226 , respectively, the lighting apparatus  200  may include a first power delivery circuit  213  and a second power delivery circuit  223 , respectively. The first power delivery circuit  213  may receive at least a part I_LED 1 ′ of the first LED driving current I_LED 1  from a first LED driver  215  and generate the positive supply voltage V_DD. For example, the first power delivery circuit  213  and the second power delivery circuit  223  may have the same or similar structure as that of the power delivery circuit  130 ′ of  FIG. 3 . 
     The peripheral component  214  may generate first control signals CTR 11  and CTR 12  to adjust the intensity of light emitted by the first LED sub-array  216  and the second LED sub-array  226 , a first control signal CTR 11  may be transmitted to the first power delivery circuit  213 , and a first control signal CTR 12  may be transmitted to the second power delivery circuit  223 . The first power delivery circuit  213  and the second power delivery circuit  223  may generate second control signals CTR 21  and CTR 22  by converting the first control signals CTR 11  and CTR 12  and may provide the second control signals CTR 21  and CTR 22  to the first LED driver  215  and the second LED driver  225 , respectively. 
     Referring to  FIG. 18B , a lighting apparatus  300  may receive the AC voltage V_AC and may include a full-wave rectifier  302 , a power delivery circuit  313 , a peripheral component  314 , first and second LED driver  315  and  325 , and first and second LED sub-arrays  316  and  326 . Compared with the lighting apparatus  200  of  FIG. 18A , the lighting apparatus  300  of  FIG. 18B  may include one power delivery circuit  313 . As shown in  FIG. 18B , the power delivery circuit  313  may receive both at least a part I_LED 1 ′ of the first LED driving current I_LED 1  and at least a part I_LED 2 ′ of the second LED driving current I_LED 2  and generate the positive supply voltage V_DD from the part I_LED 1 ′ and the part I_LED 2 ′. In some embodiments, the power delivery circuit  313  may receive only a current (e.g., I_LED 1 ′ or I_LED 2 ″) corresponding to one LED sub-array  316 , as shown in  FIG. 18B . Also, the power delivery circuit  313  may generate two or more second control signals CTR 21  and CTR 22  from one or more first control signal CTR 1 . For example, as shown in  FIG. 18B , the power delivery circuit  313  may provide the second control signals CTR 21  and CTR 22  to the first LED driver  315  and the second LED driver  325 , respectively, and the first LED driving current I_LED 1  and the second LED driving current I_LED 2  may be adjusted according to the second control signals CTR 21  and CTR 22 , respectively. 
     Although the lighting apparatuses  200  and  300  including two LED sub-arrays are shown in  FIGS. 18A and 18B , according to example embodiments of the disclosure, a lighting apparatus may include three or more LED sub-arrays. For example, a lighting apparatus may include three LED sub-arrays each including red LEDs, green LEDs, and blue LEDs, and an LED driving currents supplied to each of the three LED sub-arrays may be independently controlled according to a control signal. Also, combinations of power delivery circuits, LED drivers, and LED sub-arrays shown in  FIGS. 18A and 18B  are merely examples, and it will be understood that lighting apparatuses including different combinations from those of  FIGS. 18A and 18B  are also included in the scope of the technical idea of the disclosure. 
       FIG. 19  is a flowchart of a method of supplying power to a peripheral component in a lighting apparatus including LEDs according to an example embodiment of the disclosure. For example, the method of  FIG. 19  may be performed by the power delivery circuit  130  of  FIG. 2 . Referring to  FIG. 19 , an operating method of a lighting apparatus may include operations S 200 , S 400 , and S 600 , and  FIG. 19  will be described below with reference to  FIG. 2 . 
     In operation S 200 , an operation for receiving at least a part of an LED driving current may be performed. For example, the power delivery circuit  130  may receive at least the part I_LED′ of the LED driving current I_LED passing through the LED array  160  from the LED driver  150 . 
     In operation S 400 , an operation for generating at least one positive supply voltage and supplying the same to a peripheral component may be performed. For example, the power delivery circuit  130  may generate the positive supply voltage V_DD from the part I_LED′ provided from the LED driver  150 . Depending on the peripheral component  140 , the power delivery circuit  130  may generate a plurality of positive supply voltages. The peripheral component  140  may be operated by a positive supply voltage provided from the power delivery circuit  130 . 
     In operation S 600 , an operation for converting a control signal received from a peripheral component and providing a converted signal to an LED driver may be performed. For example, the power delivery circuit  130  may receive the first control signal CTR 1  for controlling the lighting apparatus  100  from the peripheral component  140  and generate the second control signal CTR 2  for controlling the LED driving current I_LED by converting the first control signal CTR 1 . In some embodiments, the power delivery circuit  130  may convert the first control signal CTR 1  having a variable voltage to the second control signal CTR 2  having a variable voltage or a variable current or to the second control signal CTR 2  having a non-electrical variable optical signal. The LED driver  150  may provide an adjusted LED driving current I_LED to the LED array  160  in response to the second control signal CTR 2 . 
       FIGS. 20A and 20B  are diagrams showing lighting apparatuses  400   a  and  400   b  according to example embodiments of the disclosure. Hereinafter, redundant descriptions of  FIGS. 20A and 20B  will be omitted. 
     Referring to  FIG. 20A , a lighting apparatus  400   a  may include a socket  410   a,  a power supply unit  420   a,  a heat dissipating unit  430   a,  a light source  440   a,  and an optical unit  450   a.    
     The socket  410   a  may be configured to be replaceable with a legacy lighting apparatus. Power supplied to the lighting apparatus  400   a  may be applied through the socket  410   a.  For example, an AC voltage may be applied to the socket  410   a.  As shown in  FIG. 20A , the power supply unit  420   a  may be assembled as separate units, that is, a first power supply unit  421   a  and a second power supply unit  422   a.  For example, the first power supply unit  421   a  may include the full-wave rectifier  120  of  FIG. 2 , and the second power supply unit  422   a  may include at least a portion of the LED driver  150 . As described above with reference to  FIGS. 1A and 1B , when components (e.g.,  11   a  and  13   a  of  FIG. 1 a    or  13   b  of  FIG. 1 b   ) that generate a positive supply voltage for components included in the lighting apparatus  400   a  are included, the volume of the power supply unit  420   a  may increase, and the characteristics of the lighting apparatus  400   a  may be deteriorated due to heat generated by the power supply unit  420   a.  On the other hand, as described above, according to example embodiments of the disclosure, in case of generating a positive supply voltage for a peripheral component from at least a part of the LED driving current, (e.g., by omitting the first power supply unit  421   a  or the second power supply unit  422   a ), not only the volume of the power supply unit  420   a  may be reduced, but also the deterioration of characteristics of the lighting apparatus  400   a  due to heat generation may be resolved. 
     The heat dissipating unit  430   a  may include an internal heat dissipating unit  431   a  and an external heat dissipating unit  432   a,  and the internal heat dissipating unit  431   a  may be directly connected to the light source  440   a  and/or the power supply unit  420   a,  thereby transmitting heat to the external heat dissipating unit  432   a.  Due to reduced heat generation according to an example embodiment of the disclosure, the internal heat dissipating unit  431   a  and the external heat dissipating unit  432   a  may be downsized or at least partially removed. The optical unit  450   a  may include an internal optical unit (not shown) and an external optical unit (not shown), and may be configured to evenly distribute light emitted by the light source  440   a.    
     The light source  440   a  may receive power from the power supply unit  420   a  and emit light to the optical unit  450   a.  The light source  440   a  may include a plurality of LED packages  441   a,  a circuit board  442   a,  and at least one integrated circuit package  443   a . The at least one integrated circuit package  443   a  may include at least some of a power delivery circuit, a peripheral component, and an LED driver according to example embodiments of the disclosure. 
     The plurality of LED packages  441   a  may include LED packages of the same type that emit light of the same wavelength. Alternatively, the plurality of LED packages  441   a  may include LED packages of different types that emit light of different wavelengths. For example, the LED package  441   a  may be configured to include at least one of a light emitting device that emits white light by combining yellow, green, red, or orange phosphors with a blue light emitting device and a light emitting device that emits at least one of a purple light, a blue light, a green light, a red light, or an infrared light. In this case, the lighting apparatus  400   a  may adjust the color rendering CRI to the level of sunlight in a sodium (Na) lamp, may generate white light of various color temperatures from a candlelight level (1500K) to a blue sky level (12000K), and, as occasions demand, may adjust color of light according to an ambient mood or an emotion by generating a purple, blue, green, red, or orange visible ray or an infrared ray. Also, the lighting apparatus  400   a  may generate light of a special wavelengths that may promote plant growth. 
     Referring to  FIG. 20B , a lighting apparatus  400   b  may include a socket  410   b,  a heat dissipating unit  430   b,  a light source  440   b,  and an optical unit  450   b.  Compared with the lighting apparatus  400   a  of  FIG. 20A , the lighting apparatus  400   b  of  FIG. 20B  may include the light source  440   b  implemented as a driver on board (DOB). As shown in  FIG. 20B , the light source  440   b  may include a circuit board  442   b  and includes at least one LED package  441   b,  an integrated circuit package  444   b,  and a passive device  445   b  mounted on the circuit board  442   b.  The DOB is a structure that may be efficient in terms of the productivity and the weight of the lighting apparatus  400   b,  and a circuit for supplying power to a peripheral component according to an example embodiment of the disclosure described below may facilitate the implementation of the DOB. 
     According to the example embodiments of the disclosure described above, a circuit for supplying power to peripheral components included in the lighting apparatus  400   b  provides reduced power consumption and reduced space occupancy, and thus the circuit may be mounted on the circuit board  442   b  of the DOB. In some embodiments, a peripheral component and a circuit for supplying power to the peripheral component may be included in the same integrated circuit package  444   b  as shown in  FIG. 20B . In some embodiments, the light source  440   b  may include two or more integrated circuit packages, and a peripheral component and a circuit for supplying power to the peripheral component may be included in different integrated circuit packages, respectively. Also, according to example embodiments of the disclosure, the size of the passive device  445   b  mounted on the circuit board  442   b  may also be reduced. 
     Although  FIG. 20B  shows that the heat dissipating unit  430   b  includes the internal heat dissipating unit  431   b  and the external heat dissipating unit  432   b  separated from each other, in some embodiments, the lighting apparatus  400   b  may include an integrated heat dissipating unit, and, in some other embodiments, the lighting apparatus  400   b  may not include a heat dissipating unit. In other words, according to example embodiments of the disclosure, power consumption of the lighting apparatus  400   b  may be reduced, and thus the heat dissipating unit  430   b  may be downsized or omitted. 
       FIG. 21  is a diagram showing a home-network including a lighting apparatus  520  according to an example embodiment of the disclosure. Other devices, such as a wall switch  530 , a wireless router  540 , a household electronics  570 , a door lock  580 , and a garage door  590 , may be communicate with one another via a wireless communication hub  500  by utilizing a home wireless communication protocol (e.g., ZigBee, Wi-Fi, Bluetooth, etc.). Also, a mobile phone  550  or the like may access the wireless communication hub  500  via a network  560  like the Internet. The lighting apparatus  520  may include a peripheral component for accessing the wireless communication hub  500 , and the peripheral component may receive a positive supply voltage from a power delivery circuit according to an example embodiment of the disclosure. Also, the peripheral component included in the lighting apparatus  520  may support the Internet of Things (IoT). 
     The brightness of light emitted by the lighting apparatus  520  may be automatically adjusted according to operation states of a bedroom, a living room, an entrance hall, a warehouse, a home appliance, and the surrounding environment/situation, or according to a user&#39;s control. For example, the brightness of light emitted by the lighting apparatus  520  may be automatically adjusted according to the type of a TV program broadcasted through a TV  510  or the screen brightness of the TV  510 . When human dramas are being played back and a cozy atmosphere is needed, the color temperature of light may be lowered and the color of light may be adjusted therefor. On the contrary, in case of a comedy program, the color temperature of light may be increased and the light may be adjusted to blue-based white light. 
     As described above, example embodiments have been disclosed in the drawings and specification. Although embodiments have been described herein using specific terminology, it is understood that they have been used only for purposes of describing the disclosure and not for limiting the scope of the disclosure as defined in the claims. Therefore, one of ordinary skill in the art will appreciate that various modifications and equivalent embodiments are possible without departing from the scope of the disclosure. Accordingly, the true scope of protection of the disclosure should be determined by the technical idea of the appended claims.