Patent Publication Number: US-2006013166-A1

Title: Method for determining the distance between a first and second transmitting and receiving station

Description:
The invention relates to a method for determining the distance between a first and second transmitting and receiving station according to the preamble of patent claim  1 .  
      A method of this type is known for example from DE 100 19 277 A1. In this method a radio link is established for transmitting data between an electronic key module to be carried by and on the user and an evaluation unit provided in a motor vehicle, in order to identify the key module based on an identification number stored in the key module, and to release, if necessary, the motor vehicle for use. The radio link is established here via a transmitting and receiving station provided in the key module and in the evaluation unit. To prevent the radio link from being extended via relay stations and to release the motor vehicle in this way without being noticed by the authorized user, the distance between the key module and the evaluation unit is determined and the release of the motor vehicle is prevented, if the key module is not within the immediate vicinity of the evaluation unit. In this case, determination of the distance is based on an evaluation of the signal running time of the signals transmitted via the radio link.  
      It is the object of the invention to indicate a method for determining the distance between two transmitting and receiving stations, which can be implemented at low expenditure and which enables measurement of short distances with high resolution.  
      The object is achieved by the features of patent claim  1 . Advantageous developments and further embodiments of the invention become apparent from the further claims.  
      In accordance with the invention the distance between a first and second transmitting and receiving station is determined by measuring the signal running time of a first transmission signal generated in the first transmitting and receiving station and transmitted to the second transmitting and receiving station and of a second transmission signal generated in the second transmitting and receiving station and transmitted to the first transmitting and receiving station. The first transmitting and receiving station receives the second transmission signal transmitted from the second transmitting and receiving station as a first received signal and the second transmitting and receiving station receives the first transmission signal transmitted from the first transmitting and receiving station as a second received signal. The transmission signals are respectively generated as a series of microwave pulses having a predefined pulse repetition frequency, which frequencies vary according to a predefined differential frequency value which is preferably small in relation to the impulse repetition frequencies. Furthermore, in the first transmitting and receiving station first points of coincidence are determined and in the second transmitting and receiving station second points of coincidence are determined, the first points of coincidence corresponding to those moments in time, when the pulses of the first transmission signal and the pulses of the first received signal received by the first transmitting and receiving station coincide. The signal running time of the transmission signals and thus also the distance between the transmitting and receiving stations is then determined from the distances between the points of coincidence.  
      In a preferred embodiment of the method a distance of coincidence, which represents the time offset between the first and the second points of coincidence, is determined as a measure of the signal running time of the transmission signals and thus as a measure of the distance between the two transmitting and receiving stations.  
      Preferably, for this purpose information is transmitted via the second points of coincidence via a radio channel from the second transmitting and receiving station to the first transmitting and receiving station. The distance of coincidence is then determined in the first transmitting and receiving station from the transferred information and from the first points of coincidence determined in the first transmitting and receiving station. The transmission of the information on the second points of coincidence and the transmission of the transmission signals is performed preferably via different radio channels.  
      In a further preferred embodiment of the method the second transmission signal is modulated by frequency keying of its pulse repetition frequency and a change, resulting from frequency keying, of the distance between the first points of coincidence is determined as a measure of the distance between the transmitting and receiving stations. Here, the pulse repetition frequency of the second transmission signal is preferably changed between two fixed frequency values with chronological synchronism to the second points of coincidence.  
      The two fixed frequency values are advantageously specified such that the change from one frequency value to the other frequency value causes duplication of the amount of the difference between the pulse repeat frequencies of the transmission signals or a reverse counting of this difference.  
      In an advantageous further development of the method data is transmitted from the second transmitting and receiving station to the first transmitting and receiving station by modulation of the second transmission signal. Advantageously, also the first transmission signal is modulated by frequency keying, in order to transmit data from the first transmitting and receiving station to the second transmitting and receiving station.  
      Preferably, for determining the points of coincidence in each transmitting and receiving station the transmission signal generated in the respective transmitting and receiving station is converted with the transmission signal received by this station by mixing into an intermediate frequency signal and by subsequent filtering and envelope demodulation into a pulsed evaluation signal. The pulses of the evaluation signals appear at the searched points of coincidence.  
      The method according to the invention is particularly suitable for use in a keyless locking system for motor vehicles. With a locking system of this type a base station is provided in the motor vehicle as an evaluation unit, which communicates with portable key modules via a radio link. The radio link is established via transmitting and receiving stations, which are provided in the base station and in the key modules. The radio link can be established without being noticed by the user for example by operating a door handle. Data is exchanged via the radio link, in particular identification numbers—advantageously in coded form—saved in the key modules are transmitted to the base station. The base station permits to gain access to the motor vehicle, if it recognizes on the basis of the identification number of a key module that an authorization to gain access is allocated to this key module, and if the key module is with in a certain distance to the base station. This distance is determined in accordance to the method according to the invention. Based on the high resolution it is furthermore possible to ascertain whether the key module is inside or outside the motor vehicle. Therefore, locking of the motor vehicle can be prevented, if the key module is inside the motor vehicle.  
      By taking into consideration the distance between the base station and the key module, security of the locking system is enhanced, since access to the motor vehicle is prevented also with a correct identification number, if the distance between the key module and the base station exceeds a certain value. Thus, unauthorized persons are not able to obtain access to the motor vehicle without being noticed by the authorized user, by establishing via relay stations a radio link between the key module and the base station. 
    
    
      Hereinafter the invention is further explained by the examples of embodiment taken in conjunction with the drawings.  
      FIG:  1  shows a block diagram with two transmitting and receiving stations for carrying out the method according to the invention,  
       FIG. 2  show timing diagrams of the signals generated and processed in the transmitting and receiving stations. 
    
    
      In accordance with  FIG. 1  the first transmitting and receiving station  1  and the second transmitting and receiving station  2  are identically embodied. The first transmitting and receiving station  1  comprises a highly stable oscillator  10  with frequency modulation capability, a chopper  11 , a microwave oscillator  12 , a coupler  13 , a mixer  14 , an IF-filter  15 , an IF-amplifier  18 , an envelope demodulator  16  and a transmitting and receiving antenna  17 . Accordingly, the second transmitting and receiving station  2  also comprises a highly stable oscillator  20  with frequency modulation capability, a chopper  21 , a microwave oscillator  22 , a coupler  23 , a mixer  24 , an IF-filter  25 , an IF-amplifier  28 , an envelope demodulator  26  and a transmitting and receiving antenna  27 .  
      The transmitting and receiving stations  1  and  2  are activated by an alarm process and operate simultaneously.  
      In this connection the oscillator  10  with modulation capability generates in the first transmitting and receiving station  1  an oscillator signal O 1 , which can be modulated in frequency, as an indicator of a control signal M 1 , which signal O 1  is supplied to the chopper  11 , which generates out of it a trigger signal T 1  with small impulses, which pulse distance or pulse repetition frequency fp 1  is determined by the oscillation frequency of the oscillator signal O 1 . The trigger signal T 1  is supplied to the microwave oscillator  12 , which in response to the impulses of the trigger signal T 1  generates a microwave pulse with several periods of the carrier frequency fc 1  of the oscillator  12 . The microwave oscillator  12  thus releases a series of microwave pulses as a first transmission signal S 1 , which is supplied via the coupler  13  to the transmitting and receiving antenna  17  and to the mixer  14 .  
      Analogously, the oscillator  20  with modulation capability also generates in the second transmitting and receiving station  2  an oscillator signal O 2 , which can be modulated in frequency, as an indicator of a control signal M 2 , which signal O 2  is supplied to the chopper  21 , which also generates out of it a trigger signal T 2  with small impulses, which pulse repetition frequency fp 2  is determined by the oscillation frequency of the oscillator signal O 2 . The trigger signal T 2  is supplied to the microwave oscillator  22 , which in response to the impulses of the trigger signal T 2  generates a microwave pulse with several periods of the carrier frequency fc 2  of the oscillator  22 . The microwave oscillator  22  thus releases a series of microwave pulses as a second transmission signal S 2 , which is supplied via the coupler  23  to the transmitting and receiving antenna  27  and to the mixer  24 .  
      Then, via the transmitting and receiving antennas  17  and  27  the first and second transmission signal S 1  and S 2  are transmitted to the second and first transmitting and receiving station  2  and  1  and are received there as second and first received signal E 2  and E 1  via their transmitting and receiving antennas  27  and  17  after a time lag of a signal running time τ.  
      In the first transmitting and receiving station  1  the first received signal E 1  is brought together in the mixer  14  with the first transmission signal S 1  to an intermediate frequency signal Z 1 , from which by filtering in the IF-filter  15 , amplification in the IF-amplifier  18  and subsequent demodulation in the envelope demodulator  16  a first evaluation signal D 1  is generated. Accordingly, in the second transmitting and receiving station  2  the second received signal E 2  is brought together in the mixer  24  with the second transmission signal S 2  to an intermediate frequency signal Z 2 , from which by filtering in the IF-filter  25 , amplification in the IF-amplifier  28  and subsequent demodulation in the envelope demodulator  26  a second evaluation signal D 2  is generated.  
      The signal running time τ is the time the transmission signals S 1 , S 2  require to get from one transmitting and receiving station to the other one. Based on the fixed propagation speed of electromagnetic waves it is a measure for the searched distance between the two transmitting and receiving stations  1 ,  2 .  
      The carrier frequencies fc 1 , fc 2  of the transmission signals S 1 , S 2  are identical and are, for example, in the range of several GHz. However, for the said carrier frequencies it is not much demanded with regard to their accuracy and frequency stability.  
      The width of the impulses of the trigger signals T 1 , T 2 , is in the range of approx. 1 ns and the pulse repetition frequencies fp 1 , fp 2  of the transmission signals S 1 , S 2  are in the range of, for example, several MHz. It is substantial that the pulse repetition frequencies fp 1 , fp 2  vary by a differential frequency value fd. Here, the accuracy of the distance measurement depends from the accuracy and frequency stability of the pulse repetition frequencies fp 1 , fp 2 .  
       FIG. 2  shows the diagrams of the transmission signals S 1 , S 2  transmitted from the transmitting and receiving stations  1 ,  2 , of the received signals E 1 , E 2  received by the transmitting and receiving station  1 ,  2 , of the intermediate frequency signals Z 1 , Z 2 , and of the evaluation signals D 1 , D 2  for the case that the transmitting and receiving stations  1 ,  2  are at the same place. Thus, for the signal running time τ it applies that τ=0, i.e. the transmission signals S 1 , S 2  are not delayed on the transmission path. Therefore, the first transmission signal S 1  corresponds to the second received signal E 2  and the second transmission signal S 2  corresponds to the first received signal E 1 .  
      As is implicated in the enlarged view A of section a, merely the envelopes of the signals S 1 , S 2 , E 1 , E 2  are depicted in the figure. These are impulses, which in the case of the first transmission signal S 1  and the second received signal E 2  are distanced from each other by a pulse period Tp 1  and in the case of the second transmission signal S 2  and the first received signal E 1  are distanced from each other by a pulse period Tp 2 . The pulse periods Tp 1 , Tp 2  correspond to the reciprocal value of the pulse repetition frequencies fp 1  and fp 2  of the respective signal.  
      The mixture in the mixers  14 ,  15  corresponds to a scanning of the first and second received signal E 1  and E 2  with the first and second transmission signal S 1  and S 2 . The differential frequency value fd is chosen to be such small that this is a sub-scanning.  
      The resulting evaluation signals D 1 , D 2  are also pulsed signals, which impulses appear periodically in the pulse distance Td. For the pulse distance Td it applies that Td=1/fd, fd representing the differential frequency value, by which the pulse repetition frequencies fp 1 , fp 2  vary. The pulses of the first evaluation signal D 1  appear at moments in time, at which pulses of the first transmission signal S 1  and of the first received signal E 1  coincide. Said moments in time are referred to hereinafter as first points of coincidence. Accordingly, the pulses of the second evaluation signal D 2  appear at moments in time, at which pulses of the second transmission signal S 2  and of the second received signal E 2  coincide. These moments in time are referred to hereinafter as second points of coincidence.  
      In the figure also moments in time t 01 , t 02  are shown, at which the pulses of the two transmission signals S 1 , S 2  coincide in time. These moments in time, which are also distanced from each other by the pulse distance Td, are referred to hereinafter as transmission points of coincidence.  
      With a signal running time τ=0 the first and second points of coincidence coincide with the transmission points of coincidence, as the received signals E 1 , E 2  coincide in time with the respective transmission signals S 1  and S 2 .  
       FIG. 3  shows the signals from  FIG. 2  for the case that the first received signal E 1  in relation to the second transmission signal S 2  and the second received signal E 2  in relation to the first transmission signal S 1  are time lagged on the transmission path by a signal running time τ&gt;0. Then, the evaluation signals D 1  and D 2  are shifted in relation to the transmission points of coincidence t 01 , t 02  each in different directions. The shifting direction here depends on the fact whether the first transmission signal S 1  in relation to the second transmission signal S 2  shows the higher or lower pulse repetition frequency. In the case shown the first evaluation signal D 1  is shifted to the right in relation to the transmission points of coincidence t 01 , t 02  by a first shifting value tv 1 , whereas the second evaluation signal D 2  is shifted to the left by a second shifting value tv 2 . One then obtains the moments in time till, t 12  as first points of coincidence and the moments in time t 21 , t 22  as second points of coincidence. For the shifting values tv 1 , tv 2  it applies 
   tv   1 =τ· na   1     tv   2 =τ· na   2   
 with  
       na1   =       fp1   fd     =     fp1          fp1   -   fp2                          na2   =       fp2   fd     =     fp2          fp1   -   fp2                    
 τ standing for the signal running time, fp 1  and fp 2  for the pulse repetition frequency of the first and second transmission signal S 1  and S 2  and fd for the differential frequency value. The sizes na 1 , na 2  are referred to hereinafter as gauge factors. 
 
      The pulses from the evaluation signals D 1 , D 2  are thus shifted against each other by a distance of coincidence tm=tv 1 +tv 2  determined by the signal running time τ. If the differential frequency value fd is chosen to be small in relation to the pulse repetition frequencies fp 1 , fp 2 , the gauge factors na 1 , na 2  are about the same size. For the distance of coincidence tm the following applies in approximation 
 
 tm= 2τ· na  
 
 with 
 
 na=na 1 ≈na 2 .  
 
      Based on the proportionality between the distance of coincidence tm and the signal running time τ, the signal running time τ and thus also the distance between the transmitting and receiving stations  1  and  2  can now be determined by measuring the distance of coincidence tm.  
      If the gauge factor na is chosen to be high, the measurement of the signal running time τ of the transmission signals S 1 , S 2  from an original time domain can be traced back to a time basis which is higher by several sizes in relation to the signal running time τ in a represented time domain of the evaluation signals D 1 , D 2 . For instance, the measurement of times in the size of several ns in the original time domain can be traced back to a measurement of time in the size of several μs or even ms in the represented time domain, what is combined with low technical expenditure. Consequently, with a low expenditure distances with a local resolution of approx. 10 cm can be measured, what corresponds to a time resolution of about 300 ps in the original time domain.  
      If distance measurement is to be performed at the place of the first transmitting and receiving station  1 , for determining the distance of coincidence tm at this place the first points of coincidence t 11 , t 12  as well as the second points of coincidence t 21 , t 22  are to be known or sizes are to be provided at the place of the first transmitting and receiving station  1 , which are in a certain relationship with the points of coincidence t 21 , t 22 .  
      In a first example of embodiment information is transferred from the second transmitting and receiving station  2  to the first transmitting and receiving station  1  via the two points of coincidence t 21 , t 22  via a separate radio channel, i.e. via a radio channel, which carrier frequency differs from the carrier frequency of the first and second transmission signal S 1 , S 2 . In this connection, the carrier frequency of the separate radio channel is advantageously smaller than the carrier frequency of the transmission signals S 1 , S 2 . From the first and second point of coincidence thus known at the place of the first transmitting and receiving station  1 , the distance of coincidence tm and from this the signal running time τ or the distance between the transmitting and receiving stations  1  and  2  can be determined.  
      However, the signal running time τ can also be determined by modulating the second transmission signal S 2  and by evaluating the change, resulting from the modulation, of the distance between the first points of coincidence t 11 , t 12 , . . . i.e. of the pulse distance between the pulses of the first evaluation signal D 1 , as explained in the following, or by modulating the first transmission signal S 1  and by evaluating the change, resulting from the modulation, of the distance between the second points of coincidence t 21 , t 22 , . . . i.e. the pulse distance between the pulses of the second evaluation signal D 2 .  
       FIG. 4  shows the signals from  FIGS. 2 and 3  for the case that the second transmission signal S 2  is modulated by frequency keying of the pulse repetition frequency fp 2 . Now, the pulses of the signals are merely represented by lines, which mark the moments in time the pulses appear.  
      Starting from the case that for the differential frequency value fd it applies 
 
 fd=fp   2 − fp   1  with  fp   2 &gt; fp   1 , 
 
 with frequency keying the pulse repetition frequency fp 2  of the second transmission signal S 2  surges from a first fixed frequency value f 21  by a predefined frequency step Δf to a second fixed frequency value f 22 =f 21 +Δf, i.e. the differential frequency value fd is multiplied, or is reduced from the second frequency value f 22  to the first frequency value f 21 . Frequency keying is performed here with chronological synchronism to the pulses of the second evaluation signal D 2 . 
 
      In the shown example the pulse repetition frequency fp 2  is switched over to the points of coincidence t 22 , t 24 . In the time segments A the pulse repetition frequency fp 2  is then equal to the first frequency value f 21  and in the time segment B it is equal to the second frequency value f 22 . The consequence of the frequency jumping by the frequency step Δf is that the pulse distance Td between the pulses of the second evaluation signal D 2  is reduced by frequency keying from value m to value n and in turn is increased from value n to value m. If the frequency step Δf—as in shown in the figure—is chosen to be equal to the value 
 
Δ f=f 2     1   −fp   1 = fd,  
 
 the amount of the differential frequency value 
 
 fd=|fp   1   −fp   2 |
 
 is doubled when passing over from the time segment A into the time segment B and is halved again when passing from the time segment B into the next time segment A. Therefore, the value m is twice as high as the value n. 
 
      A further consequence of frequency keying is that with the up-keying of the pulse repetition frequency fp 2  to the second fixed frequency value f 22  the pulse distance Td between the pulses of the first evaluation signal D 1  is reduced by a distance proportional time td from the value m to a value x. Accordingly with the back-keying of the pulse repetition frequency fp 2  to the first fixed frequency value f 21  and based on the increase of the pulse distance Td between the pulses of the second evaluation signal D 2  of the pulse distance Td between the pulses of the first evaluation signal D 1  is increased by the distance proportional time td from value n to a value y.  
      For the values x and y it applies  
       x   =     m   -   td         
         y   =     n   +   td       ,     
     ⁢   with       
       td   =       τ   ·   na2     =       τ   ·     f21     f21   -   fp1         =     τ   ·       f21   fd     .               
 
 Here, m and n stand for the long or short pulse distance Td between the pulses of the second evaluation signal D 2 , td for the distance proportional time, τ for the signal running time and na 2  for the gauge factor with the pulse repetition frequency fp 2 =f 21 . The values x and y are thus linearly dependent from the signal running time τ. 
 
      The above equation is valid for high gauge factors na 2  and for a frequency step of Δf=f 21 −fp 1 =fd. If the frequency step Δf is optionally chosen, it applies  
       td   =       2   ·     (       τ   ·   na2     -     τ   ·     na2   *         )       =     2   ·   τ   ·     (     na2   -     na2   *       )             
     with     
       na2   =     f21     f21   -   fp1           
         na2   *     =       f22     f22   -   fp1       =         f21   +     Δ   ⁢           ⁢   f         f21   +     Δ   ⁢           ⁢   f     -   fp1       .           
 
      Here, na 2  and na 2 * stand for the gauge factors with the pulse repetition frequency fp 2 =f 21  and fp 2 =f 22 =f 21 +Δf, respectively.  
      Consequently, by measuring the values x and y it is possible to determine the distance proportional time td and from it the signal running time τ as well as the distance between the transmitting and receiving stations  1  and  2 .  
      Apart from determination of the signal running time τ the described method simultaneously permit also to transfer data from the second transmitting and receiving station  2  to the first transmitting and receiving station  1 . For this purpose it is merely necessary to respectively allocate one of the logical values “0” or “1” to the values m and n. Then, the logical value of the value m is to be allocated to the value x and the logical value of the value n to the value y. In like manner by frequency keying also data can be transferred from the first transmitting and receiving station  1  to the second transmitting and receiving station  2 .  
      Based on frequency keying at the outputs of the mixers  14 ,  24  two intermediate frequencies f=fc/na 2 , fi*=fc/na 2 * varying from each other are produced, fc standing for the carrier frequency of the transmission signals S 1 , S 2 , so that the IF-filters  15 ,  25  each must show two pass-bands.  
      This disadvantage is avoided by choosing the frequency step Δf such that frequency keying effects reverse counting of the difference between the pulse repetition frequencies fp 1 , fp 2 . The frequency values f 21 , f 22  are to be chosen such that the pulse repetition frequency fp 1  is in the middle of these values.  
      For a frequency keying of this type  FIG. 5  shows the transmission signals S 1 , S 2 , the received signals E 1 , E 2  and the evaluation signals D 1 , D 2  for the case that the pulse repetition frequency fp 2 =fp 21 =fp 1 −fd is keyed to a value fp 22 =fp 21 +Δf=fp 1 +fd, i.e. with Δf=2·fd. Here the case is shown for a signal running time τ=0. In this case the frequency step Δf does not change the pulse distance Td between the pulses of the evaluation signals D 1 , D 2 .  
       FIGS. 6   a  and  6   b  show equal signals for a signal running time τ&gt;0. In the time segment A the pulse repetition frequency fp 2  of the second transmission signal S 2  is equal to the first frequency value f 21  and in the time segment B it is equal to the second frequency value f 22 =f 21 +Δf. The change of frequency from frequency value f 21  to frequency value f 22  happens at the moment in time t 21  and the change of frequency from frequency value f 22  back to the frequency value f 21  at the moment in time t 24 , i.e. synchronously to the pulses of the second evaluation signal D 2 .  
      The change of frequency does change the amount of the distance of coincidence tm, merely the direction of the offset between the evaluation signals D 1 , D 2 , i.e. the sign of the phase difference between these signals changes. Therefore, when changing from the first frequency value f 21  to the second frequency value f 22 , the pulse distance between the pulses of the first evaluation signal D 1  is one-time reduced from value Td to value U=2tm=4 τ na and when changing back to the first frequency value f 21  is one-time increased to value d=2Td-U. The change, resulting from frequency keying, of the pulse distance between the pulses of the first evaluation signal D 1  thus dependents on the signal running time τ. Measuring the pulse distances between the pulses of the first evaluation signal D 1  permits to determine the values U or D and to determine from it the signal running time τ and the distance between the transmitting and receiving stations  1 ,  2 .  
      This type of frequency keying is particularly suitable for the serial transfer of digital data. Merely one of the logical values “0” or “1” is to be allocated to the frequency values f 21 , f 22  as is shown in  FIG. 7 .  
      According to  FIG. 7 a  digital data signal Dx is transmitted from the second transmitting and receiving station  2  to the first transmitting and receiving station  1 , by setting the pulse repetition frequency fp 2  of the second transmission signal S 2  in time segments A, in which a logical value “0” is to be transferred, onto the first frequency value f 21  and in time segments B, in which a logical value “1” is to be transferred, onto the second frequency value F 22 . In the first transmitting and receiving station  1  based on the pulse distance between the pulses of the first evaluation signal D 1  it is recognized whether a bit value in the data signal Dx has changed. If the pulse distance shortens to a value U being below the period Td, this is an indication of a bit value change from “0” to “1”, whereas this is an indication of a bit value change from “1” to “0”, if the pulse distance extends to a value D being above the period Td. In like manner also the first transmission signal S 1  can be modulated by frequency keying, ensuring a bi-directional data transfer between the transmitting and receiving stations  1 ,  2 .  
      Based on the periodicity of the transmission signals S 1 , S 2  the described methods provide clear results of measurement merely for signal running times τ, which are within a region of unambiguousness determined by the pulse repetition frequencies fp 1 , fp 2 . Indeed, the region of unambiguousness can be increased by changing the pulse repetition frequencies fp 1 , fp 2 , for example by frequency division, however, this involves a reduction of the measurement resolution.  
      Exceeding the region of unambiguousness during a measurement can be recognized by means of an additional measurement, by increasing the region of unambiguousness for the additional measurement by changing the pulse repetition frequencies fp 1 , fp 2  and by testing whether the result of the additional measurement is within the region of unambiguousness of the one measurement.