Patent Publication Number: US-2020278419-A1

Title: Method for suppresing noise and increasing speed in miniaturized radio frequency signal detectors

Description:
CROSS REFERENCE TO RELATED APPLICATIONS 
     This application is a Continuation application of U.S. application Ser. No. 16/645,718, filed Mar. 9, 2020, which is a national phase application of PCT/HR2019/000004, filed Feb. 28, 2019, wherein the entire content and disclosure of each of the foregoing applications is incorporated by reference into the present application. 
    
    
     FIELD OF INVENTION 
     The invention relates to radio frequency (RF) signal detectors that incorporate digital signal processing (DSP) unit. Such detectors are usually used in a spectral analyzer instruments and in radar signal detectors. 
     SUMMARY OF INVENTION 
     Radar signal detectors use various techniques to scan radio frequency spectrum and to detect radiation in their field of view. There are several methods for implementation of such detectors and most recently more and more devices are implemented as software defined radio (SDR) with digital processing of received signals. Digital processing enables a detector to extract detected radar&#39;s frequency spectrum signature and then process this signature to determine if it&#39;s a valid speed measuring radar signature, a signal of interest, or if it belongs to a source of no interest, for instance a vehicle inbuilt collision avoidance radar, door opener radar or other sources. SDR approach requires wide baseband channel and processing in software, and as bandwidth of the baseband into analog to digital converter (ADC) is much wider than in traditional detectors, interference and noise problems are also significantly more difficult. For multiple band detectors that use multiple local oscillators (LO) or detectors with multiple mixing (down-converting) stages problem is even bigger and will introduce false detections and consequently decreased sensitivity. Shielding and infilling with absorbing materials helps in suppression of interference and crosstalk but requires additional space on device circuit boards, larger housing and will add additional cost. Advanced approach of LO signal generators combining to suppress interference and crosstalk by smart choice of LO frequency pairs in the detector down-converter stages can be applied to suppress interference and crosstalk. This method will eliminate unwanted interference and images from mixing products in down-converter mixers and combined with filtering of out-of-band components will result in clean baseband signal with only wanted signal converted to the digital domain. 
     Once signals are converted to the digital domain additional processing steps can be applied to distinguish the signal type and to determine if the user is to be alarmed or if the signal is of no interest. The most complex task of this process is to distinguish modulated Frequency Shift Keying (FSK) or Frequency Modulated Continuous Wave (FMCW) speed measuring radar signals from the signals of vehicle inbuilt anti-collision or inbuilt adaptive cruise control radars. As new models of radars are continuously introduced to the market, both speed measuring and vehicle inbuilt or for other applications of no interest to a user of the detector, classification is quite complex and maintaining of a database is very demanding task with almost certainty missing some signatures in the database eventually. To overcome this problem in the detector is used artificial intelligence (AI) method that can learn signatures and to determine with some level of certainty on the type of unknown signatures. AI processing module is fed with spectral signatures detected in the signal detector module and signatures are analyzed over time to determine various parameters changes over time and this information is used to determine on the signature type. Combination of Support Vector Machine and Deep Learning methods are used in the AI module and are combined with dynamical database of known signatures for signals of interest and signals of no interest. Learning process is continuously active during operation of the detector and is continuously upgrading its knowledge database. Usually the detector is used in semi-supervised mode of learning, but it can be also switched to completely unsupervised mode. In the semi-supervised mode predefined known signatures database is used and during the operation of the device a user is able to manually classify detected signals enhancing the learning process for new signatures. Learning modes can be configured and user can determine the acceptable level of distraction for semi-supervised mode. Such approach has significantly higher reliability in classification of radar signatures and will miss significantly lower number of speed measuring radar detections, with significantly reduced number of false alarms caused by vehicle inbuilt radars, door opener radars, traffic counter radars, or other signals on no interest. 
     PERVIOUS STATE OF ART 
     In a radio frequency (RF) signal detectors designed to scan a wide frequency band common implementation is comprising two local oscillator (LO) signal generators and down-conversion that is done in two steps. This architecture is used to minimize bandwidth of IF signals and to simplify implementation of circuits. Downside of the architecture is usually significant intermodulation and spurious emissions for some combinations of LO generator frequencies as the effect of crosstalk. Intermodulation and crosstalk in general degrade the performance of the detector and prevents proper operation or significantly affects receiver sensitivity for some combinations of frequencies. Additionally, this effect can manifest false detections of the detector. Crosstalk and intermodulation are usually solved by isolating, shielding and filtering but this can be quite difficult when small dimension of the circuit, small device mass or very low cost is desired. 
     In the past decade speed measuring radars have significantly evolved technologically and now measure not only a vehicle speed but also its location on the road (so called 3D radars). These new features became possible by change in the radar operation principle from traditional continuous wave single frequency Doppler to modulated waveform in most cases FSK or FMCW. These radar types have ability to detect and measure speeding vehicles in scenarios not previously possibly such as in a dense traffic, to precisely locate and capture better quality images and even can be used in the multiple lane roads to detect and track multiple vehicles simultaneously. Not only the speed measuring radars technology has evolved but also frequency bands used by it has also changed and now spans from 10.5 GHz to 36.1 GHz with three distinct bands being: X band 10.5-10.55 GHz, K band 24.0-24.25 GHz and Ka band 33.3-36.1 GHz. Such distribution of speed measuring radars frequency poses a requirement for detectors to have 3 band receivers with very wide bands. Detector bandwidth in the X band needs to be at least 50 MHz, in the K band at least 250 MHz and in the Ka band at least 2800 MHz. As speed measuring radars can also be implemented as short on time pulse radars (so called POP) with active signal time measured in milliseconds, scanning of all bands must be very fast to enable detection of such short pulses. Bringing together all above requirements for a detector into a single device is difficult, especially by using traditional narrow frequency scanning method with threshold peak detector and is the reason why more and more detector devices are presently implemented as SDR. Such detectors are tracking over time signal shape or distribution of energy in the frequency spectrum and are determining the type of signal based on those parameters. If valid speed measuring radar is determined from signal frequency spectrum and time tracking then alarm is given and forwarded to user interface (UI) and is usually accompanied with information of detected signal type, frequency, strength etc. Alarming of a user is based on the detected signatures and can be implemented in a way that any detection will automatically lead to an alarm, which is how the older generation detectors work, or it can be done in a more sophisticated way with additional processing steps to minimize false alarms towards a user but while still alarming for each detected signal of interest—speed measuring radar. True/false alarms ratio is very important parameter for high-end detectors as it is directly related to usability of the device. With present situation where almost every new passenger vehicle has at least one and very often several inbuilt radars for safety or autonomous driving, usability of traditional detectors that will alarm a user on any detected signal is poor. 
     Signal signature classification in present state of the art radar detectors requires large database of known signal signatures. It can be implemented as positive signatures database where all known speed measuring radars signatures are stored and if received signature is not found in the database it means it is of no interest and is discarded. In this case average number of false alarms will be low but there is significant probability of missing real signal of interest detections caused by a non-current database. The other approach is to have negative signatures database and to discard only detected signal signatures that are found in this database and known as signals of no interest. This approach will generate more false alarms as it is almost impossible to maintain negative signatures database properly but will produce better probability of speed measuring radar detection. Some present detectors also use combination of positive and negative databases to lower the number of unknown signatures and to improve ratio between true and false alarms. In all above cases present state of art SDR detectors require a significant amount of work to maintain the databases and keep the true and false alarms ratio in acceptable level. 
     Additional feature commonly used is to discard some alarms as false by knowing the location of a detection and comparing the location to a database of known false alarm locations. This feature does not help in a case of moving false alarm sources like the beforementioned vehicle inbuilt radars. 
     Due to the national regulations some frequency bands or segments and some speed measuring radar types are not present on some geographical locations and some detectors use this information in the form of another database to further improve the true/false alarms ration but again the feature does not help in the case of moving false alarm sources. 
     Maintenance of such mentioned databases is significant work either for a manufacturer or for a user of the detector. The quality of the databases directly translates to the usability of the device and to user experience. Databases that are not updated, with lot of missing signatures will lead to degradation of the true/false alarms ratio and detector quality perception degradation. 
     DETAILED DESCRIPTION OF THE INVENTION 
     A method for suppressing noise and increasing speed in miniaturized radio frequency signal detectors has been disclosed. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         FIG. 1  shows a block diagram of the circuit with a single RF input band and two down-converting mixer stages that are controlled by a DSP unit. 
         FIG. 2  shows a block diagram of the circuit with a dual RF input bands and two down-converting mixer stages that are controlled by a DSP unit. 
         FIG. 3  shows a block diagram of the circuit with a triple RF input bands and two down-converting mixer stages that are controlled by a DSP unit. 
         FIG. 4  discloses the flow chart describing the calibration process during which noise and coefficient values are measured and stored into a device&#39;s memory. 
         FIG. 5  shows a sample table of intermodulation intensities for single input channel. 
         FIG. 6  shows a sample table of intermodulation intensities for two input channels. 
         FIG. 7  shows a sample table of intermodulation intensities for three input channels. 
         FIG. 8  discloses the flow chart describing classification method for radar signal detectors with AI aided signature classification. 
         FIG. 9  discloses the flow chart describing detail flow diagram of AI classification with dynamical database updating and retraining process for SVM and neural network for automatic performance upgrade. 
     
    
    
     The primary objective of the present invention is to enable construction of miniaturized RF signal detectors where space considerations prohibit isolation, shielding and absorbing as primary solutions to intermodulation noise produced by multiple LO generators working at different frequencies in a tight space. The invention solves this problem by using the disclosed method of using a DSP to control the LO generators where DSP has a program logic and a memory of prestored values and by using those can always set the down-conversion in a manner resulting in minimal intermodulation noise. 
     Secondary objective is to enable fastest possible scanning of two or more RF bands in a signal detector where bands have different bandwidths and one of the bands is down-converted by using the beforementioned dual stage mixing process. Uniform scanning of all bands wider and narrower is also achieved by disclosed method that uses a DSP controlled LO generators. 
     An additional objective is to enable differentiating the received signals to signals of interest and signals of no interest or noise by implementing an artificial intelligence (AI) algorithm in the DSP. Disclosed method presents an extra step in suppressing unwanted or noise signals. 
     In the approach with two LO signal generators and two consecutive mixer stages a circuit is designed in a way that for each desired frequency or frequency band in the RF input signal a down-conversion to baseband is possible with various possible combinations of LO 1  and LO 2  frequencies that all give same sum frequency. In such approach it is also possible to select a pair of frequencies LO 1  and LO 2  out of all possible pairs for each RF or RF band that also results in eliminated or minimized intermodulation noise. 
     Microwave frequency generators and mixers, as well as strip-line conductors do not have perfectly flat characteristics over usable frequency range so changing two mixer stages as described above does result in combined characteristic being different for different LO 1  and LO 2  pairs even that sum frequency of down-conversion is the same. 
     Selection of the best pairs of the frequencies for LO generators out of a union of all possible segment pairs is process done offline, measured on several temperatures and input power supply voltage as all those parameters can affect quality of selected pair. The procedure is comprised of signal recording for all possible pairs in the complete frequency range and measurement of parameters for each segment. 2D table shown on the  FIG. 5  is created and stored to the DSP memory by division of the segment peak value with segment average noise value. 
     Optimal asset allocation algorithm is applied to the stored table to select best LO frequency pairs, cells with minimal value of calculated ratio between peak and average noise value, with uniform distribution of scanning along the frequency bandwidth. Thresholding is applied to eliminate every cell (frequency pair) where ratio is bigger than 1 and all other cells are valid choice for the scanning pattern. Scanning pattern is created in the way that cell (frequency pair) with minimal value is used for each requested segment following uniform scanning distribution across all frequency bands. Sorting is applied to the selected scanning pattern to further minimize number of frequency changes for both generators. Resulting array with selected LO frequency pairs for all segments is than stored in the DSP memory and is used in the real-time operation of the device. 
     Similar process is possible for dual and three channel receiver and example of 2D intermodulation table measured offline and used for selection of LO pairs is shown on  FIG. 6  for dual channel receiver and on  FIG. 7  for three channel receivers. All three examples on  FIGS. 5 to 7  are measured with same process and only difference is selection of the value for each cell. In two and three channel case maximum value from the two or three measured is used for all LO combinations where multiple valid values are possible. If due to the combination of LO frequencies one or more channels is sampled out of the band of interest, then measured value for that channel is ignored. 
       FIG. 8  is presenting high level diagram of the classification method for in-vehicle radar detectors with AI aided signature classification. Signal is analyzed in the signal analyzer module depending on the detector architecture and spectral signature is delivered to AI module. Signal signature is consisting of spectral power distribution (spectral peaks list) with frequencies, amplitudes and phase for each detected peak. Signature is being delivered to the AI module all the time it is being detected, and AI is tracking spectral changes over time. Alarms are issued by the AI to the user over a user interface (UI) on detected signals of interest. Together with decision making on detected signal type AI module is also constantly calculating score of the classification which is reflecting how certain the classification is. The ones with a high score are also resulting in an update to the dynamic signature database. In another embodiment the classification method is using positive and negative database of verified signatures and it is also implementing a user interface (UI) for a user to classify manually of detected signals. In a case when a user classifies detected signal manually, signature for this signal is added to dynamic database with a high score. 
     Detailed operation of AI module and internal architecture is shown on  FIG. 9  where is visible that AI module consists of two parts. First part is slower, heuristics-based detector implemented with neural network, and other part is machine learning model, specifically Support Vector Machine. Machine learning model for classification of signal signatures is initially learned using sufficient set of signal signatures labeled as positives and negatives. On each detected signal during operation of the detector if calculated score of a classification is above a set threshold the signal signature is added to the dynamic database and SVM is retrained with new updated database. Weight factor for all dynamically added signatures is low so the impact of this signatures would not have big effect on the SVM training by itself but with accumulation over time it will affect training of the SVM more and more and contribute to improved detection rate of signals of interest. This approach assures that a small number of possibly wrong classifications will not lead to a generally poor detection rate of the SVM. For those classified signatures that had a lower score than a threshold, the neural network is applied as these signatures are considered significantly different than information already in the SVM database. Neural network is pretrained to track and classify signatures with deep learning principle. Classification and score from neural network are then used for update of dynamic database with even lower weight factor but enabling device to slowly learn completely new signatures that appear to be speed measuring radar signals or other signals of interest. Neural network is also periodically retrained with new dynamic database but for this training process only signatures classified by SVM or users&#39; inputs are used. 
     Preferred Embodiment 
     The circuitry and the functional detail of the preferred embodiment in accordance with the invention will be explained in detail in the following paragraphs. 
     In the preferred embodiment as shown in  FIG. 1 , a circuit is comprised of input RF antenna ( 112 ) feeding the input of a low noise amplifier (LNA) ( 105 ) and output of LNA is feeding a first stage mixer ( 103 ). In the preferred embodiment application, a high bandwidth detector antenna is designed in a way that it also acts as bandpass filter so the discrete bandpass filter before the first LNA is omitted. First mixer ( 103 ) receives LO signal from the first generator ( 101 ) on the LO port ( 108 ) and input RF signal on the RF port ( 112 ) and is producing an intermediate frequency (IF) signal on its IF port. IF signal is than fed to an IF bandpass filter ( 113 ) to extract only the desired signal bandwidth. IF bandpass filter ( 113 ) is defining the possible scan range for the first generator ( 101 ) and good practice is to have this filter as wide as possible to allow scanning of the whole frequency range, but still narrow enough to keep signal noise as low as possible. Filtered IF signal is than amplified with the amplifier ( 116 ) and filtered again with bandpass filter ( 114 ). This amplified and filtered signal is fed to the RF input port of the second mixer ( 104 ). LO port of the second mixer is fed with the second generator&#39;s ( 102 ) output and resulting mixer IF signal after the second down-conversion is the baseband signal ( 104 ) on the output port. Baseband signal ( 104 ) is amplified ( 117 ), filtered ( 115 ) and analog to digital converted (ADC) with ADC 1  ( 106 ). Digital stream from ADC 1  ( 106 ) is delivered to DSP circuit ( 107 ) and used for further signal processing in digital domain. 
     Additional RF channel is added to a circuit on  FIG. 1 , as shown in  FIG. 2  with additional RF input comprising of input antenna ( 207 ) and low noise amplifier ( 202 ) followed by signal combiner ( 203 ) where two input signals are combined prior to the first mixing ( 222 ) additional possibility to scan two channels in parallel is possible on the detector. For efficient operation usually one of these channels has significantly wider bandwidth. In a receiver as shown on the  FIG. 2  additional dependency is introduced between a generator  1  ( 216 ) and a generator  2  ( 217 ) causing further reduction in possible valid frequency pairs for two generators LO signals. IF signal of the first mixer ( 222 ) is split to baseband of the first RF input channel ( 212 ) practically creating direct down-conversion receiver and on the same spot IF for the second wider RF channel is extracted and forwarded to the second mixer. Baseband of the first channel ( 212 ) is amplified ( 225 ) and filtered ( 228 ) after the splitter ( 204 ) and converted by ADC 1  ( 205 ) to digital domain. Filtering on the baseband side after the first mixer will eliminate out-of-band unwanted signal but interference and crosstalk with frequency range falling in the channel bandwidth will stay and must be eliminated by selection of LO frequencies. IF channel of the second RF input is after splitter ( 204 ) amplified ( 224 ) and filtered ( 227 ) and mixed ( 223 ) with signal generated by the second ( 217 ) LO signal generator. Filtering of IF signal ( 213 ) between the first mixer ( 222 ) and the second mixer ( 223 ) will eliminate all out-of-band unwanted signals but would not have effect on signals in the channel bandwidth. Output of the second mixer ( 223 ) is baseband for the second RF input and is amplified ( 226 ), filtered ( 229 ) and converted to digital domain with ADC 2  ( 206 ). Same effect as for the first channel will be achieved with filtering on the baseband side and same problem with intermodulation and crosstalk falling in the channel bandwidth will stay. Additional digital processing steps are done in the DSP module ( 207 ) for both signals. 
     Selection of the best pairs of the frequencies for LO generators out of a union of all possible segment pairs is process done offline, measured on several temperatures and input power supply voltage as all those parameters can affect quality of selected pair. The procedure is comprised of signal recording for all possible pairs in the complete frequency band for both RF channels and measurement of quality parameters for each segment. 2D table shown on the  FIG. 5  is created and stored to the DSP memory by division of the segment peak value with segment average noise value for booth channels and bigger value is selected representing worse case for those combination of frequency pairs. For pairs that are not resulting with proper channel selection for both channels as one of the channels, usually narrower band one, will be out-of-the-band for such combination, the value for valid channel is used. Optimal asset allocation algorithm is applied to the stored table to select best LO frequency pairs, cells with minimal value of calculated ratio between peak and average noise value, with uniform distribution of scanning along the frequency bandwidth for both channels and uniform repetition of scanning for both channels. Sorting is applied to the selected scanning pattern to further minimize number of frequency changes for both generators with additional restriction to maintain uniform scanning for both channels. Resulting array with selected LO frequency pairs for all segments is than stored in the DSP memory and is used in the real-time operation of the device. 
     By adding an additional RF input ( 301  &amp;  302 ), additional mixer ( 303 ), baseband processing hardware comprising of amplifier ( 334 ), bandpass filter ( 335 ), ADC 3  ( 304 ) and without adding another LO signal generator, it is possible to realize a detector embodiment with three RF inputs scanning, as shown on  FIG. 3 . In this detector device RF channel  1  and RF channel  3  are narrower band than wideband RF input channel  2 . Crosstalk and intermodulation in this embodiment would also pose a problem if the disclosed method would not be applied, causing a poor sensitivity or improper detection alarms. Filtering on baseband side prior to the analog to the digital conversion is used to eliminate most of the intermodulation and image signals falling out-of-band, but crosstalk and intermodulation in band will appear in the channel bandwidth. Those intermodulation and crosstalk components that will fall in the channel band are eliminated/minimized with same method as for single or dual channel system. Selection of best scanning sequence for LO signal generators is again possible, but again with additional restrictions due to the limiting factors of different bandwidths for different channels since uniform repetition of segments scanning for all channels is required. 
     Selection of the best pairs of the frequencies for LO generators out of a union of all possible segment pairs is again process done offline, measured on several temperatures and input power supply voltage as all those parameters can affect quality of selected pair. The procedure is comprised of signal recording for all possible pairs in the complete frequency band for all three RF channels and measurement of quality parameters for each segment. 2D table shown on the  FIG. 6  is created and stored to the DSP memory by division of the segment peak value with segment average noise value for all channels and maximal value is selected representing worse case for those combination of frequency pairs. For pairs that are not resulting with proper channel selection for all channels as one of the channels, usually narrower band one, will be out-of-the-band for such combination, the maximal value for valid channels is used. Optimal asset allocation algorithm is applied to the stored table to select best LO frequency pairs, cells with minimal value of calculated ratio between peak and average noise value, with uniform distribution of scanning along the frequency bandwidth for all channels and uniform repetition of scanning for all channels. Sorting is applied to the selected scanning pattern to further minimize number of frequency changes for both generator generators with even more restriction to maintain uniform scanning for all three channels. Resulting array with selected LO frequency pairs for all segments is than stored in the DSP memory and is used in the real-time operation of the device. 
     The following is the procedure of calibration of noise values for all possible LO segment pairs and temperatures that is performed beforehand and the values stored in the memory of the DSP unit, as shown on the  FIG. 4 :
       401     

     Calibration starts by reading the system temperature and saving it to variable T_amb
       402     

     Loop L1 counter is setup to the lowest frequency of the PLL1 ( 101 ) 
     L1_c:=PLL1_start
       403     

     Loop L2 counter is setup to the lowest frequency of the PLL2 ( 102 ) 
     L2_c:=PLL2_start
       404     

     Both PLLs are tuned: PLL1 ( 101 ) is tuned to the current value stored in L1_c, and PLL2 ( 102 ) is tuned to the current value stored in L2_c
       405     

     1 millisecond of data samples received on ADC ( 106 ) are stored into temporary memory buffer mem[1 . . . N]
       406     

     Data in memory buffer is converted to amplitudes of spectral representation of the signal by using FFT algorithm 
     mem:=abs(FFT(mem)) 
     A maximum value is determined in the signal spectra 
     peak:=max(mem) 
     An average value of the signal spectra is calculated 
     avg:=sum(mem)/N 
     An coefficient representing amount of intermodulation is calculated 
     imod_cf:=peak/avg
       407     

     A tuple consisting of (T_amb, L1_c, L2_c, imod_cf) is stored into device memory
       408     

     Loop L2 counter is incremented
         L2_c:=L2_c+L2_step         409     

     Test whether loop L2 has covered the complete frequency range of PLL2
         repeat until L2_c&gt;=PLL2_end         410     

     Loop L1 counter is incremented
         L1_c:=L1_c+L1_step         411     

     Test whether loop L1 has covered the complete frequency range of PLL1
         repeat until L1_c&gt;=PLL1_end       

     Described calibration procedure produces a table of values of intermodulation noise for every pair of LO frequency segments of both generators for the whole LO frequency ranges. Sample tables are shown on  FIGS. 5 .,  6 . and  7 . 
       FIG. 5 . shows a table sample of intermodulation intensities for single input channel, depending on tuning frequencies of PLL1 and PLL2. PLL1 frequencies change over rows, while PLL2 frequencies change over columns. For clearer presentation, the actual values for each segment are omitted; instead, the segments where the intermodulation intensity value exceed a critical threshold of 1.0 are marked in black. The combination of PLL1 and PLL2 frequencies that result in a segment marked in black contain too much intermodulation noise and should be skipped.
       501  Intermodulation intensity values in the first row were measured by setting PLL1 frequency to PLL1_start.     502  Intermodulation intensity values in the second row were measured by setting PLL1 frequency to PLL1_start+PLL1_step.     503  Intermodulation intensity values in the last row were measured by setting PLL1 frequency to PLL1_end.     504  Intermodulation intensity values in the first column were measured by setting PLL2 frequency to PLL2_start.     505  Intermodulation intensity values in the last column were measured by setting PLL2 frequency to PLL2_end.     506  Segments with intermodulation intensities above 1.0 are marked in black.   
       FIG. 6 . shows a table sample of intermodulation intensities for two input channels, depending on tuning frequencies of PLL1 and PLL2. PLL1 frequencies change over rows, while PLL2 frequencies change over columns. For clearer presentation, the actual values for each segment are omitted; instead, the segments where the intermodulation intensity value of either channel  1  or channel  2  exceeds a critical threshold of 1.0 are marked in black. The combination of PLL1 and PLL2 frequencies that result in a segment marked in black contain too much intermodulation noise and should be skipped.
       601  Intermodulation intensity values in the first row were measured by setting PLL1 frequency to PLL1_start.     602  Intermodulation intensity values in the last row were measured by setting PLL1 frequency to PLL1_end.     603  Intermodulation intensity values in the first column were measured by setting PLL2 frequency to PLL2_start.     604  Intermodulation intensity values in the last column were measured by setting PLL2 frequency to PLL2_end.   

       FIG. 7 . shows a table sample of intermodulation intensities for three input channels, depending on tuning frequencies of PLL1 and PLL2. PLL1 frequencies change over rows, while PLL2 frequencies change over columns. For clearer presentation, the actual values for each segment are omitted; instead, the segments where the intermodulation intensity value of any of the three channels exceeds a critical threshold of 1.0 are marked in black. The combination of PLL1 and PLL2 frequencies that result in a segment marked in black contain too much intermodulation noise and should be skipped.
       701  Intermodulation intensity values in the first row were measured by setting PLL1 frequency to PLL1_start.     702  Intermodulation intensity values in the last row were measured by setting PLL1 frequency to PLL1_end.     703  Intermodulation intensity values in the first column were measured by setting PLL2 frequency to PLL2_start.     704  Intermodulation intensity values in the last column were measured by setting PLL2 frequency to PLL2_end.   
     After signals are down-converted by proposed single, dual or three channel detector circuit with intermodulation and crosstalk reduction additional steps of digital signal processing is applied. Detection of the signals can be observed in three groups that are implemented in digital signal processing: short pulses detection (POP signals), CW (continuous wave) detection, 3D or modulated signals detection. The first two groups are relatively simple to detect by tracking of the received signal in time and by applying rule of single spectrum peak to the detection. Modulated signals are much more complex to detect as there will be several or large number of peaks in the spectrum and waveform of such signals is varying through time. For such signals special detection algorithm is implemented that is tracking signal peak distribution in the frequency spectrum of the signal and is tracking the changes of this frequency spectrum peak distribution through time. Distribution of the frequency spectrum peaks of the signals is also shortly called spectrum signature or signal signature. 
     Classification of the spectrum signature is important feature for an in-vehicle radar detectors as it is important to distinguish between vehicle inbuilt anti-collision and adaptive cruise control radars integrated in more and more modern vehicles and speed measuring radars that are usually mounted aside the road or overhead the traffic lanes. Due to a large number of both inbuilt radars and speed measuring radars and new models being introduced to the market daily, it is very complex task to develop classification of those signals based on only known radars signatures and such approach would certainly miss detections of all new radars not already in the signature database. 
     Artificial intelligence (AI) supported classification of detected signals is implemented in a digital signal processing unit ( 107 ) for the purpose of alarming a user of detected speed measurement radar signals and discarding other detected signals arriving from other sources, wherein SVM (Supported Vector Machine) ( 913 ) is used for classification of detected signals, and the SVM is initially trained from a database of known signals belonging to speed measuring radars and to other non-interesting sources, and where the SVM is dynamically retrained when an unknown signal is detected and classified by AI neural network ( 910 ) with high confidence, resulting in better specialization of the SVM model and giving better classification results from then on. 
     Signal signature ( 902 ) is used as the input to the SVM classificatory ( 913 ) and each SVM classification is accompanied by certainty score. When certainty score for a received signal is above a set threshold, classification is considered as signal of interest, a signal signature is added to the dynamic database ( 911 ). When, for a received signal signature, certainty score is under a threshold, heuristics part of AI module implemented with neural network ( 910 ) is employed to classify the signal signature. If classification of heuristic algorithm is considered confident enough, this signature with neural network ( 910 ) classification is added to dynamic signature database ( 911 ) but with lower score. SVM ( 913 ) is than retrained periodically so that new signal signatures are accounted for, and that accuracy of classification is increased. 
     Heuristic algorithm in the AI ( 808 ) module used for classification of unknown signals is neural network ( 910 ) with deep-learning method ( 912 ) used for training. On the input of neural network spectrum signature ( 903 ) is applied with up to 128 spectral peaks consisting of spectral peak amplitude and frequency. If spectral signature ( 903 ) is composed by lower number of spectral peaks than only those extracted from the signal are used and the rest is set to zero. Neural network ( 910 ) is processing the inputs and output ( 904 ) is composed by two numbers, where the first is binary number 1 or 0 signaling with 1 speed measuring radar classification and with 0 other radar type classification. The second output number is integer signaling confidence prediction in the range from 0 to 100. Training of the neural network ( 910 ) is done in the laboratory by presenting to the input of the network large number of known signal signatures and compering the output with known classification. Parameters of each neuron element in the neural network are than changed to get better classification for each sample and better convergence for the whole sample set in general. Control set of signal signatures with known classification that were not used in training process is used to check classification during the training process. Training process in iteratively repeated until satisfactory result of classification on whole training and check set are achieved. 
     During the operation of the detector neural network ( 910 ) is periodically retrained with updated training set stored in the dynamical database ( 911 ) together with preconfigured verified database of known signatures. For training of the neural network ( 910 ) only signatures classified with SVM ( 913 ) with sufficient classification score are used. 
     To aid even better true/false alarm ratio and to improve dynamical database ( 911 ) creation and training process for both SVM ( 913 ) and neural network ( 910 ) it is possible to add interaction with user through system UI (User Interface). The feedback from the user is used to manually classify alarms (accept/reject) and information if available can be used for supervised learning mode. Process is done similarly to the unsupervised mode without user interaction where SVM ( 913 ) is used for classification of detected signals, and the SVM ( 913 ) is initially trained from a database of known signals belonging to speed measuring radars and to other non-interesting sources. When an unknown signal is detected, classification by neural network ( 910 ) is used and if high confidence is achieved signature is added to dynamical signature database ( 911 ), resulting in better specialization of the SVM ( 913 ) model and giving better classification results after retraining. In supervised mode, user interaction is used to confirm/reject AI classification and the signature is stored to the dynamical signature database ( 911 ) with much higher score than only AI classified signatures ( 803 ), resulting in more impact to the retraining process of SVM ( 913 ) and neural network ( 910 ) and thus better classification of similar signal signatures from now on. 
     For proposed detector device with function of suppressing of RF interference to increase sensitivity of RF receiver circuit with single, dual or three channels it is important to use DSP module with possibility to control 2 separate PLL LO signal generators, interface one, two or three fast analog to digital converters with sufficient bandwidth and dynamical signal range for proper signal signature extraction even for low power and weak signals. 
     RF receiver circuit of detector is required to achieve sufficient sensitivity for wideband channels and filtering of out-of-band components has to be implemented efficient enough that components of intermodulation that are falling out-of-band do not create additional aliasing and interference in the desired frequency band. 
     It should be understood that the invention is not limited by the embodiments described above, but is defined solely by the claims.