Patent Publication Number: US-6906569-B2

Title: Digital signal delay device

Description:
The invention relates to a digital signal delay device in accordance with the preamble of claim  1 . 
   In semiconductor elements, delay lock loops are often used for generating the internal clock. These consist e.g. of many delay members that are connected in series. 
   A delay member serves to apply a delay to a digital signal available at the input of the delay member, so that a digital output signal may be tapped at the output of the delay member, said output signal being delayed vis-à-vis the input signal, but corresponding to it otherwise. 
   A delay member may e.g. consist of two inverters connected in series, in particular CMOS inverters. The input of the first inverter forms the input, and the output of the second inverter forms the output of the delay member, the output of the first inverter being connected to the input of the second inverter. 
   When the state of the signal available at the input of the delay member or of the first inverter, respectively, changes, e.g. from “logically low” to “logically high” (—or vice versa from “logically high” to “logically low”—), the signal at the output of the first inverter (and accordingly also the signal at the input of the second inverter) changes—after a predetermined delay time t a —its state from “logically high” to “logically low” (—or vice versa from “logically low” to “logically high”—). 
   Consequently, the signal at the output of the second inverter or at the output of the delay member, respectively, changes—again after a predetermined delay time t b —its state from “logically low” to “logically high” (—or vice versa from “logically high” to “logically low”—). 
   The signal at the output of the delay member thus corresponds to the signal at its input, with the exception that it is delayed vis-à-vis thereto by a—total—signal delay time of T=t a +t b . 
   To provide an element or a signal delay device, respectively, with adjustable signal delay time, a plurality of delay members of the above-mentioned type may be connected in series. 
   The signal at the output of the n-th delay member is delayed by n×T vis-à-vis the signal at the input of such a signal delay device. 
   The outputs of the delay members may—except with the respectively following delay member—additionally be connected with the (total) output of the signal delay device, e.g. by means of corresponding transfer gates. 
   By means of the transfer gates, that delay member may be selected, the output signal of which is to be connected through to the output of the signal delay device. 
   This way, the delay of the (total) output signal can be adjusted with respect to the signal available at the input of the signal delay device or at its first delay member, respectively. 
   By means of a signal delay device of the above-mentioned type, the total signal delay which is applied to the input signal is, however, adjustable with relatively coarse exactness only. 
   It is an object of the invention to provide a novel digital signal delay device. 
   This and further objects of the invention are achieved by the subject matter of claim  1 . 
   Advantageous further developments of the invention are indicated in the subclaims. 
   In accordance with a basic idea of the invention, a digital signal delay device is provided for converting a signal (IN) to a delayed signal (OUT) corresponding thereto, said device comprising a plurality of signal delay elements connected in series, wherein, depending on the desired delay of the delayed signal (OUT), the output signal of a particular signal delay element is respectively used for generating the delayed signal (OUT), and wherein each of the signal delay elements comprises one single inverter only. 
   Depending on the respectively desired delay, the output signal of the respective signal delay element used for generating the delayed signal (OUT) may then be inverted or not inverted vis-à-vis the signal (IN). 
   Of advantage is a development where the signal delay elements are respectively connected with corresponding switching devices, wherein—depending on the respectively desired delay—that switching device is activated that is connected with the signal delay element whose output signal is to be used for generating the delayed signal (OUT). 
   Preferably—depending on whether the output signal of a particular signal delay element is inverted or not inverted vis-à-vis the signal (IN)—the switching device connected with the respective signal delay element is correspondingly designed such that—on activation—it advances the output signal in a non-inverted or in an inverted manner. 
   The result is that the respectively advanced, delayed signal corresponds to the signal (IN)—which is e.g. available at the input of the signal delay device—(i.e. is identical, or alternatively complementary thereto), and has an—adjustable—delay vis-à-vis to it (namely a delay which substantially corresponds to the delay time of the output signal of that signal delay element whose output signal is—possibly in inverted form—advanced via the corresponding switching device. 
   Since the corresponding signal delay elements each only comprise one single inverter, and not e.g. two inverters connected in series, the respectively desired delay time can be adjusted substantially more accurately or precisely than with conventional digital signal delay devices. 

   
     In the following, the invention will be explained in more detail by means of several embodiments and the enclosed drawing. The drawing shows: 
       FIG. 1  a schematic representation of a circuit arrangement of a digital signal delay device according to prior art; 
       FIG. 2  a schematic representation of a circuit arrangement of a digital signal delay device in accordance with an embodiment of the present invention; 
       FIG. 3  a schematic representation of an inverter circuit arrangement used as a gate of the first kind with the digital signal delay device illustrated in  FIG. 2 ; 
       FIG. 4  a schematic representation of a transfer gate circuit arrangement used as a gate of the second kind with the digital signal delay device illustrated in  FIG. 2 ; 
       FIG. 5   a  a schematic representation of a gate of the first kind used with an alternative embodiment of a signal delay device, and of a tristate inverter additionally connected behind the respective gate of the first kind. 
       FIG. 5   b  a schematic representation of a gate of the second kind used with the alternative embodiment of a signal delay device, and of a tristate inverter additionally connected behind the gate; 
       FIG. 6   a  a schematic representation of a gate of the first kind used with a modification of the alternative embodiment, and of a transfer gate connected therebehind, and of a tristate inverter; and 
       FIG. 6   b  a schematic representation of a gate of the first kind used with the modification of the alternative embodiment, which is used instead of the gate of the second kind as illustrated in  FIG. 5   b , and of two tristate converters connected therebehind. 
   

     FIG. 1  shows a schematic representation of a circuit arrangement of a digital signal delay device  1  in accordance with prior art. 
   The signal delay device  1  serves to apply an—adjustably high—delay to a digital signal IN available at an input  2   a  of the signal delay device  1 , so that a digital signal OUT—which is delayed vis-à-vis the input signal IN—can be tapped at the output  2   b  of the signal delay device  1 . 
   As is shown in  FIG. 1 , the signal delay device  1  comprises a plurality of signal delay elements  3   a ,  3   b ,  3   c ,  3   d ,  3   e  connected in series. The number n of signal delay elements  3   a ,  3   b ,  3   c ,  3   d ,  3   e  is—as will be explained in detail below—chosen as a function of that signal delay that is to be obtained maximally with the signal delay device  1 . 
   The first signal delay element  3   a  is connected with the input  2   a  of the signal delay device  1  via a line  4   a , and—via a line  4   b —with the input of the second signal delay element  3   b . The output of the second signal delay element  3   b  is connected to the input of the third signal delay element  3   c  via a line  4   c . Correspondingly, the output of the third signal delay element  3   c  is connected with the input of a further (not illustrated) signal delay element via a line  4   d , etc. 
   As is further shown in  FIG. 1 , the input of the signal delay element  3   d  is connected to the output of a preceding (not illustrated, either) signal delay element via a line  4   e , and the input of the signal delay element  3   e  is connected to the output of the signal delay element  3   d  via a line  4   f.    
   Each signal delay element  3   a ,  3   b ,  3   c ,  3   d ,  3   e  comprises two inverters  5   a ,  5   b , or  6   a ,  6   b , or  7   a ,  7   b , or  8   a ,  8   b , or  9   a ,  9   b , connected in series. 
   The input of the respectively first inverter  5   a ,  6   a ,  7   a ,  8   a ,  9   a  of each signal delay element  3   a ,  3   b ,  3   c ,  3   d ,  3   e  forms the respective input of the corresponding signal delay element  3   a ,  3   b ,  3   c ,  3   d ,  3   e  (i.e. is connected with the corresponding line  4   a ,  4   b ,  4   c ,  4   e ,  4   f ), and the output of the respectively first signal delay element inverter  5   a ,  6   a ,  7   a ,  8   a ,  9   a  is connected with the respective input of the respectively second signal delay element inverter  5   b ,  6   b ,  7   b ,  8   b ,  9   b  via corresponding connecting lines  10 ,  11 ,  12 ,  13 ,  14 . The output of the respectively second inverter  5   b ,  6   b ,  7   b ,  8   b ,  9   b  of each signal delay element  3   a ,  3   b ,  3   c ,  3   d ,  3   e  forms the respective output of the corresponding signal delay element  3   a ,  3   b ,  3   c ,  3   d ,  3   e  (i.e. is connected with the corresponding line  4   b ,  4   c ,  4   d ,  4   f ). 
   When the state of the signal IN available at the input of the first signal delay element  3   a  or its first inverter  5   a , respectively, changes e.g. from “logically low” to “logically high” (—or vice versa from “logically high” to “logically low”—), the signal at the output of the first signal delay element inverter  5   a  (and accordingly also the signal at the input of the second signal delay element inverter  5   b ) changes—after a certain delay time t a —its state from “logically high” to “logically low” (—or vice versa from “logically low” to “logically high”—). Consequently, the signal at the output of the second signal delay element inverter  5   b  or at the output of the first signal delay element  3   a , respectively, changes—again after a certain delay time t b —its state from “logically low” to “logically high” (—or vice versa from “logically high” to “logically low”—). 
   The signal at the output of the second signal delay element inverter  5   b  or of the first signal delay element  3   a , respectively (and thus also the signal at the input of the second signal delay element  3   b  or its first inverter  6   a , respectively) thus corresponds to the signal IN at the input of the first signal delay element  3   a  or its first inverter  5   a , respectively, with the exception that it is delayed vis-à-vis thereto by a—total—delay element signal delay time of T=t a +t b . 
   As has been explained above, the remaining signal delay elements  3   b ,  3   c ,  3   d ,  3   e  have a structure that is correspondingly identical to that of the first signal delay element  3   a.    
   Consequently—when the state of the signal available at the respective input of the respective signal delay element  3   b ,  3   c ,  3   d ,  3   e  or its respectively first inverter  6   a ,  7   a ,  8   a ,  9   a  changes e.g. from “logically low” to “logically high” (—or vice versa from “logically high” to “logically low”—)—again after a particular delay element (total) signal delay time T—the signal at the output of the respective signal delay element  3   b ,  3   c ,  3   d ,  3   e  or its respectively second inverter  6   b ,  7   b ,  8   b ,  9   b  also changes its state from “logically low” to “logically high” (—or vice versa from “logically high” to “logically low”—). 
   The signal available e.g. at the output of the second signal delay element  3   b  (and thus also the signal at the input of the third signal delay element  3   c  or its first inverter  7   a , respectively) thus corresponds to the signal IN at the input of the first signal delay element  3   a  or its first inverter  5   a , respectively, with the exception that it is delayed vis-à-vis thereto—in total—by a total signal delay time of T+T=2T (the signal at the output of the n-th signal delay element thus corresponds—generally speaking—to the signal IN at the input of the signal delay device  1 , with the exception that it is delayed vis-à-vis thereto—in total—by a total delay time of n×T). 
   As is further illustrated in  FIG. 1 , the output of the first signal delay element  3   a  is—except that it is connected via the line  4   b  with the input of the second signal delay element  3   b —additionally connected via a line  15   a  with the input of a first gate, e.g. a transfer gate  16   a.    
   Correspondingly, the outputs of the remaining signal delay elements  3   b ,  3   c ,  3   d ,  3   e  each are also connected with the input of corresponding further gates, in particular transfer gates  16   b ,  16   d ,  16   e , via corresponding lines  15   b ,  15   d ,  15   e.    
   The outputs of the transfer gates  16   a ,  16   b ,  16   d ,  16   e  are connected via corresponding lines  17   a ,  17   b ,  17   d ,  17   e  to a line  18  which is connected with the output  2   b  of the signal delay device  1 . 
   Corresponding control signals C 1 , C 2 , . . . , C n−1 , C n  are applied to the control inputs  19   a ,  19   b ,  19   d ,  19   e  of the transfer gates  16   a ,  16   b ,  16   d ,  16   e , as will be explained in detail further below. In the case of a “logically low” control signal C 1 , C 2 , . . . , C n−1 , C n  the respective transfer gate  16   a ,  16   b ,  16   d ,  16   e  is in a “locked” state, and in the case of a “logically high” control signal C 1 , C 2 , . . . , C n−1 , C n  it is in a “conductive” state. In the case of a “conductive” state, the signal available at the input of the respective transfer gate  16   a ,  16   b ,  16   d ,  16   e  is connected through to its output (and in the case of a “locked” state disconnected from the transfer gate output). 
   By the fact that respectively one of the control signals C 1 , C 2 , . . . , C n−1 , C n  is selected such that it is in a “logically high” state, and the respective other control signals C 1 , C 2 , . . . , C n−1 , C n  are selected such that they are in a “logically low” state, that signal delay element  3   a ,  3   b ,  3   c ,  3   d ,  3   e  may be selected whose output signal is to be connected through to the output  2   b  of the signal delay device  1 . 
   The signal OUT that is output at the output  2   b  of the signal delay device  1  is thus applied with a delay vis-à-vis the signal at the input  2   a  of the signal delay device  1 , said delay corresponding to the delay time of the output signal of that signal delay element  3   a ,  3   b ,  3   c ,  3   d ,  3   e  whose output is just being connected through to the output  2   b  of the signal delay device  1  via the corresponding transfer gate  16   a ,  16   b ,  16   d ,  16   e  (plus the delay time of the respective transfer gate  16   a ,  16   b ,  16   d ,  16   e  connected through). 
     FIG. 2  shows a schematic representation of a circuit arrangement of a digital signal delay device  101  in accordance with an embodiment of the present invention. 
   The signal delay device  101  may e.g. be installed in a DRAM memory element based e.g. on CMOS technology (or in any other element). It serves to apply an—adjustably high—delay to a digital signal IN available at an input  102   a  of the signal delay device  101 , so that a digital signal OUT—delayed vis-à-vis the input signal IN—can be tapped at the output  102   b  of the signal delay device  101 . 
   As is illustrated in  FIG. 2 , the signal delay device  101  comprises a plurality of signal delay elements  103   a ,  103   b ,  103   c ,  103   d ,  103   e  that are connected in series. The number n of signal delay elements  103   a ,  103   b ,  103   c ,  103   d ,  103   e  is as will be explained more exactly further below—selected as a function of that signal delay that is to be achieved maximally with the signal delay device  101 . 
   The first signal delay element  103   a  is connected via a line  104   a  with the input  102   a  of the signal delay device  101  and—via a line  104   b —with the input of the second signal delay element  103   b . The output of the second signal delay element  103   b  is connected to the input of the third signal delay element  103   c  via a line  104   c . Correspondingly, the output of the third signal delay element  103  is connected via a line  104   d  with the input of a further (not illustrated) signal delay element, etc. 
   As is further illustrated in  FIG. 2 , the input of the signal delay element  103   d  is connected via a line  104   e  to the output of a preceding (not illustrated, either) signal delay element, and the input of the signal delay element  103   e  is connected via a line  104   f  to the output of the signal delay element  103   d.    
   Each signal delay element  103   a ,  103   b ,  103   c ,  103   d ,  103   e  comprises—different from the signal delay device illustrated in FIG.  1 —only one single inverter  105 ,  106 ,  107 ,  108 ,  109  (instead of two inverters connected in series), wherein the input of the respective inverter  105 ,  106 ,  107 ,  108 ,  109  forms the respective input of the corresponding signal delay element  103   a ,  103   b ,  103   c ,  103   d ,  103   e  (i.e. is connected with the corresponding line  104   a ,  104   b ,  104   c ,  104   e ,  104   f ), and wherein the output of the respective inverter  105 ,  106 ,  107 ,  108 ,  109  forms the respective output of the corresponding signal delay element  103   a ,  103   b ,  103   c ,  103   d ,  103   e  (i.e. is connected with the corresponding line  104   b ,  104   c ,  104   d ,  104   f ). 
   When the state of the signal IN available at the input of the signal delay device  101  (and thus at the input of the first signal delay element  103   a  or the inverter  105 , respectively) changes e.g. from “logically low” to “logically high” (—or vice versa from “logically high” to “logically low”—), the signal at the output of the first signal delay element  103   a  or of the inverter  105 , respectively (and accordingly also the signal at the input of the second signal delay element  103   b  or of the inverter  106 , respectively) changes—after a certain delay time t—its state from “logically high” to “logically low” (—or vice versa from “logically low” to “logically high”—). 
   The signal at the output of the first signal delay element  103   a  or of the inverter  105 , respectively, thus corresponds to the signal IN at the input of the first signal delay element  103   a  or of the inverter  105 , respectively, with the exception that it is inverted and delayed by a delay time t vis-à-vis thereto. 
   When, as explained above,—after the delay time t—the signal at the output of the first signal delay element  103   a  (or of the inverter  105 , respectively) and accordingly also the signal at the input of the second signal delay element  103   b  (or of the inverter  106 , respectively) changes its state from “logically high” to “logically low” (—or vice versa from “logically low” to “logically high”—), the signal at the output of the second signal delay element  103   b  or of the inverter  106 , respectively, changes—again after a certain delay time t—its state from “logically low” to “logically high” (—or vice versa from “logically high” to “logically low”—). 
   The signal at the output of the second signal delay element  103   b  or of the inverter  106 , respectively, thus corresponds to the signal IN at the input of the first signal delay element  103   a  or of the inverter  105 , respectively, with the exception that it is delayed vis-à-vis thereto—in total—by a delay time of t+t=2t. 
   As has been explained above, the remaining signal delay elements  103   c ,  103   d ,  103   e  are of a structure that is correspondingly identical to that of the first two signal delay elements  103   a ,  103   b.    
   Due to the respectively inverting, delayed advancement of the digital signal that is respectively available at the input of the corresponding signal delay element  103   c ,  103   d ,  103   e  (as explained in analogy above with respect to the two signal delay elements  103   a ,  103   b ) by the respective signal delay element  103   c ,  103   d ,  103   e , the signal at the output of the n-th signal delay element  103   c ,  103   d ,  103   e  thus corresponds, generally speaking, to the signal IN at the input  102   a  of the signal delay device  101 , with the exception that it is
     i) delayed vis-à-vis the signal IN by a total delay time of n×t,
 
and possibly—and only with such signal delay elements  103   c ,  103   d  in which n is an odd number—that it is
   ii) inverted vis-à-vis the signal IN.   

   As is further shown in  FIG. 2 , the output of the first signal delay element  103   a  or of the inverter  105 , respectively, is—except that it is connected via the line  104   b  with the input of the second signal delay element  103   b  or of the inverter  106 , respectively—additionally connected via a line  115   a  with the input of a gate  116   a  “of the first kind”, as will be explained more exactly in the following. 
   In a correspondingly similar way is the output of the second signal delay element  103   b  or of the inverter  106 , respectively, connected via a line  115   b  with the input of a gate  116   b  “of the second kind”, as will be explained more exactly in the following. 
   Correspondingly, the outputs of the remaining signal delay elements  103   c ,  103   d ,  103   e  each are connected via corresponding lines  115   d ,  115   e  with the respective input of corresponding further gates  116   d ,  116   e , namely, generally speaking, the respective outputs of those signal delay elements  103   c ,  103   d  in which n is an odd number are connected with the input of a corresponding gate  116   d  “of the first kind”, and the outputs of those signal delay elements  103   c ,  103   d  in which n is an even number are connected with the input of a corresponding gate  116   e  “of the second kind”. 
   In the present embodiment, e.g. the inverter circuit arrangement (in particular a tristate inverter circuit arrangement) illustrated in detail in  FIG. 3  is e.g. used as a gate  116   a ,  116   d  “of the first kind”, and the transfer gate circuit arrangement illustrated in detail in  FIG. 4  is e.g. used as a gate  116   b ,  116   e  “of the second kind”. 
   As is illustrated in  FIG. 4 , the transfer gate circuit arrangement of the gates  116   b ,  116   e  “of the second kind” comprises an n-channel field effect transistor  120   a  and a p-channel field effect transistor  120   b.    
   The control signal C 2  available at a control input  119   b  of the respective gate  116   b ,  116   e  is—via a control line  121   a —supplied to the gate of the n-channel field effect transistor  120   a.    
   Furthermore, the control signal C 2  available at the control input  119   b  of the respective gate  116   b ,  116   e  is additionally—via a line  121   b —supplied to the input of an inverter  122 , and the control signal /C 2  output at the output of the inverter  122  and complementary to the control signal C 2  is supplied to the gate of the p-channel field effect transistor  120   b.    
   As is further illustrated in  FIG. 4 , the drains of the n- or p-channel field effect transistors  120   a ,  120   b , respectively, are connected via a line  123  with one another and additionally to the line  115   b  (and thus form the input of the transfer gate circuit arrangement). 
   Furthermore, the sources of the n- or p-channel field effect transistors  120   a ,  120   b , respectively, are connected with one another via a line  124 , and additionally with a line  117   b  that is connected to a line  118  (and thus form the output of the transfer gate circuit arrangement). 
   The following effect is achieved thereby: As soon as the control signal C 2  available at the control input  119   b  of the gate  116   b  changes its state from “logically low” to “logically high” (and thus the complementary control signal /C 2  changes its state from “logically high” to “logically low”), the signal available at the input of the transfer gate circuit arrangement or of the gate  116   b , respectively, i.e. at the line  115   b , is connected through to the output of the transfer gate circuit arrangement or of the gate  116   b , i.e. to the line  117   b.    
   When then the signal available at the control input  119   b  of the gate  116   b  again changes its state from “logically high” to “logically low” (and thus the complementary control signal /C 2  changes its state again from “logically low” to “logically high”), the signal available at the input of the transfer gate circuit arrangement or of the gate  116   b , respectively, i.e. at the line  115   b , is again disconnected galvanically from the output of the transfer gate circuit arrangement or of the gate  116   b , respectively, i.e. from the line  117   b.    
   The gates  116   a ,  116   d  “of the first kind” have a structure that is different from that of the gate  116   b  “of the second kind” illustrated in FIG.  4 . In accordance with the (tristate) inverter circuit arrangement illustrated in detail in  FIG. 3 , they comprise each two n-channel field effect transistors  126   a ,  126   b  and two p-channel field effect transistors  125   a ,  125   b.    
   The n-channel field effect transistor  126   a  and the p-channel field effect transistor  125   a  have a connection similar to a conventional, simple inverter, with the exception that the drain of the n-channel field effect transistor  126   a  is not directly connected to the supply voltage, but by interconnection of the n-channel field effect transistor  126   b , and that the drain of the p-channel field effect transistor  125   a  is not directly connected to the mass, but by interconnection of the p-channel field effect transistor  125   b.    
   As is illustrated in  FIG. 3 , the drain of the n-channel field effect transistor  126   a  is—via a line  127 —connected to the source of the n-channel field effect transistor  126   b , and the drain of the n-channel field effect transistor  126   b  is—via a line  128 —connected to the supply voltage. 
   Furthermore, the drain of the p-channel field effect transistor  125   a  is connected—via a line  129 —to the source of the p-channel field effect transistor  125   b , and the drain of the p-channel field effect transistor  125   b  is connected—via a line  130 —to the mass. 
   As is further illustrated in  FIG. 3 , the gates of the n- or p-channel field effect transistors  125   a ,  126   a , respectively, are connected with one another via a line  132 , and are additionally connected to the line  115   a  (and thus form the input of the (tristate) inverter circuit arrangement). 
   Furthermore, the sources of the n- or p-channel field effect transistors  125   a ,  126   a , respectively, are connected with one another via a line  131 , and are additionally connected with a line  117 —which is also connected to the line  118  (and thus form the output of the (tristate) inverter circuit arrangement). 
   The control signal C 1  available at a control input  119   a  of the respective gate  116   a ,  116   d  is—via a control line  133   a —supplied to the gate of the n-channel field effect transistor  126   b.    
   Furthermore, the control signal C 1  available at the control input  119   a  of the respective gate  116   a ,  116   c  is additionally supplied to the input of an inverter  134  via a line  133   b , and the control signal /C 1  that is output at the output of the inverter  134  and that is complementary to the control signal C 1  is additionally supplied to the gate of the p-channel field effect transistor  125   b.    
   The following effect is achieved thereby: As soon as the control signal C 1  available at the control input  119   a  of the gate  116   a  changes its state from “logically high” to “logically low” (and thus the complementary control signal /C 1  changes its state from “logically low” to “logically high”), the n- and the p-channel field effect transistors  125   b ,  126   b  are switched off (and thus the simple inverter formed by the n- and the p-channel field effect transistors  125   a ,  126   a  is disconnected from the supply voltage or mass, respectively, i.e. de-activated). The signal available at the input of the (tristate) inverter circuit arrangement or of the gate  116   a , respectively, i.e. at the line  115   a , then has no influence on the signal available at the output of the (tristate) inverter circuit arrangement or of the gate  116   a , respectively, i.e. at the line  117   a.    
   When the control signal C 1  available at the control input  119   a  of the gate  116   a  then changes its state from “logically low” to “logically high” (and thus the complementary control signal /C 1  changes its state from “logically high” to “logically low”), the n- and the p-channel field effect transistors  125   b ,  126   b  are switched on (and thus the simple inverter formed by the n- and the p-channel field effect transistors  125   a ,  126   a  is connected with the supply voltage or the mass, respectively, i.e. is de-activated). 
   Due to the two n- and p-channel field effect transistors  125   a ,  126   a  forming a simple inverter, the signal available at the input of the gate  116   a , i.e. at the line  115   a , is advanced in inverted form to the output of the gate  116   a , i.e. to the line  117   a , with the respectively one of the field effect transistors  125   a ,  126   a  constituting the load resistance for the respectively other field effect transistor  125   a ,  126   a.    
   As is illustrated in  FIG. 2 , the corresponding outputs are (in a corresponding manner to the first and second gates  116   a ,  116   b ), also with the remaining gates  116   d ,  116   e , connected via corresponding lines  117   d ,  117   e  to the line  118  which is connected to the output of the signal delay device  101 . 
   As has already been mentioned above, corresponding control signals C 1 , C 2 , . . . , C n−1 , C n  are applied to the control inputs  119   a,    119   b,    119   d,    119   e  of the gates  116   a,    116   b,    116   d,    116   e,  namely such that respectively one of the control signals C 1 , C 2 , . . . , C n−1 , C n  is in a “logically high” state, and the respectively other control signals C 1 , C 2 , . . . , C n−1 , C n  are in a “logically low” state. 
   In this way, that signal delay element  103   a,    103   b,    103   c,    103   d,    103   e  may be selected whose output signal—possibly in inverted form (namely in the case of signal delay elements  103   c ,  103   d  where n is an odd number)—is to be connected through to the output  102   b  of the signal delay device  101 . 
   Due to the inverted through-connection achieved by the gates  116   a ,  116   d  and the non-inverted through-connection achieved by the gates  116   b ,  116   e  of the signal that is output by the respectively selected signal delay element  103   a ,  103   b ,  103   c ,  103   d ,  103   e , it is achieved that the signal OUT that is output at the output  102   b  of the signal delay device  101  corresponds to the signal IN at the input  102   a  of the signal delay device  101 ; it is, however, applied with an—adjustable—delay vis-à-vis thereto (namely with a delay corresponding to the delay time of the output signal of that signal delay element  103   a ,  103   b ,  103   c ,  103   d ,  103   e  whose output—possibly in inverted form—is just being connected through via the corresponding gate  116   a ,  116   b ,  116   d ,  116   e  to the output  102   b  of the signal delay device  101  (plus the delay time of the respectively active gate  116   a ,  116   b ,  116   d ,  116   e )). 
   The respectively desired delay time between the input signal IN and the output signal OUT can be adjusted substantially more accurately or precisely than with the signal delay device  1  illustrated in  FIG. 1  (namely in time steps of a dimension of t and not in time steps of a dimension of T=t a +t b ). 
   In order to improve the characteristics of the signal delay device  101  illustrated in  FIGS. 2 ,  3 , and  4  with respect to the respectively occurring capacitive loads, in the case of an alternative embodiment—with otherwise identical structure of the signal delay device  101 —in accordance with  FIGS. 5   a ,  5   b , an additional tristate inverter circuit arrangement  135 ,  136  may be connected between the output of each gate  116   a ,  116   b ,  116   d ,  116   e  (irrespective of whether “of the first kind” or “of the second kind”) and the corresponding line  117   a ,  117   b ,  117   d ,  117   e  corrected with the line  118 . 
   The respectively interposed tristate inverter circuit arrangement  135 ,  136  has a structure that corresponds to the structure of the tristate inverter circuit arrangement illustrated in FIG.  3  and acting as a gate  116   a  “of the first kind” there. 
   By means of the interposition of the above-mentioned tristate inverter circuit arrangements  135 ,  136  it is achieved that the circuits driving the lines  118  (here: the tristate inverter circuit arrangements  135 ,  136 )—irrespective of which one of the gates  116   a ,  116   b ,  116   d ,  116   e  is just activated by applying a corresponding “logically high” control signal C 1 , C 2 , . . . , C n−1 , C n —all have an identical structure, and that thus—irrespective of which one of the gates  116   a ,  116   b ,  116   d ,  116   e  is activated—a respectively identical capacitive load results. 
   In a modification of the above-mentioned alternative embodiment (i.e. in a further alternative embodiment), a transfer gate circuit arrangement  137  may, in accordance with  FIG. 6   a , be connected between the output of each gate  116   a ,  116   d  “of the first kind” and the corresponding additional tristate inverter circuit arrangement  135  connected with the corresponding line  117   a ,  117   d , wherein said transfer gate circuit arrangement  137  may have the same structure as the transfer gate circuit arrangement illustrated in FIG.  4  and acting as a gate  116   b  “of the second kind” there. 
   Furthermore, in this further alternative embodiment according to  FIG. 6   b , the above-mentioned gates  116   b ,  116   e  “of the second kind” may be replaced by corresponding gates  139  “of the first kind” (which may have a structure corresponding to that of the tristate inverter circuit arrangement illustrated in FIG.  3 ), and a respectively further tristate inverter circuit arrangement  138  (which may also have a structure corresponding to that of the tristate inverter circuit arrangement illustrated in FIG.  3  and acting as a gate  116   a  “of the first kind” there) may be connected between these gates  139  “of the first kind” and the corresponding additional tristate inverter circuit arrangement  136  connected with the respective line  117   b ,  117   e.    
   The—interposed—transfer gate  137  illustrated in  FIG. 6   a  may be designed such that the signals are advanced in such a delayed manner by the transmission gate  137  that the—total—delay time occurring during the advancement of the corresponding signals by the gate  116   a , the transfer gate circuit arrangement  137 , and the tristate inverter circuit arrangement  135  illustrated in  FIG. 6   a  is as great as the—total—delay time occurring during the advancement of the corresponding signals by the gate  139 , and the two tristate inverter circuit arrangements  138 ,  136  illustrated in  FIG. 6   b.