Patent Publication Number: US-11392156-B2

Title: Voltage generator with multiple voltage vs. temperature slope domains

Description:
FIELD OF THE INVENTION 
     The present application generally pertains to voltage generators, and more particularly to voltage generators which generate voltages across a wide range of temperatures. 
     BACKGROUND OF THE INVENTION 
     Bandgap voltage generators may be used to generate reference voltages which have a desired dependence on temperature. For example, bandgap voltage generators may generate reference voltages which have approximately zero voltage depends over a particular temperature range of interest. 
     BRIEF SUMMARY OF THE INVENTION 
     One inventive aspect is an electronic circuit. The electronic circuit includes a reference voltage generator, which includes a first candidate circuit configured to generate a first candidate reference voltage, a second candidate circuit configured to generate a second candidate reference voltage, and a selector circuit configured to select one of the first and second candidate reference voltages. The electronic circuit also includes a third circuit configured to generate a power supply voltage based on the selected candidate reference voltage. 
     In some embodiments, the first candidate circuit is configured to cause the first candidate reference voltage to change by an first amount in response to changing a temperature from a first temperature value to a second temperature value, the second candidate circuit is configured to cause the second candidate reference voltage to change by an second amount in response to changing the temperature from the first temperature value to the second temperature value, and the first amount is greater than the second amount. 
     In some embodiments, the second amount is substantially zero. 
     In some embodiments, at temperatures which are greater than a crossover temperature, the first candidate reference voltage is greater than the second candidate reference voltage, at temperatures which are less than the crossover temperature, the first candidate reference voltage is less than the second candidate reference voltage, and, at the crossover temperature, the first candidate reference voltage is equal to the second candidate reference voltage. 
     In some embodiments, the selector circuit is configured to select a maximum of the first candidate reference voltage and the second candidate reference voltage. 
     In some embodiments, the third circuit is configured to receive the selected candidate reference voltage. 
     In some embodiments, the third circuit is configured to receive a level shifted version of the selected first or second candidate voltage. 
     In some embodiments, the third circuit includes a voltage regulator. 
     In some embodiments, the voltage regulator is configured to generate the power supply voltage for a digital circuit and an analog circuit. 
     In some embodiments, at temperatures which are greater than a crossover temperature, the first candidate reference voltage is greater than the second candidate reference voltage, at temperatures which are less than the crossover temperature, the first candidate reference voltage is less than the second candidate reference voltage, and, at the crossover temperature, the first candidate reference voltage is equal to the second candidate reference voltage. 
     In some embodiments, the electronic circuit is specified to function at a particular temperature value less than the crossover temperature, the first candidate circuit is configured to generate the first candidate reference voltage with a particular reference voltage value at the particular temperature, the voltage regulator is configured to generate the power supply voltage with a particular power supply voltage value in response to receiving a voltage of the particular reference voltage value, and the analog circuit is configured to not function with the particular power supply voltage value at the particular temperature. 
     Another inventive aspect is a method of operating an electronic circuit. The electronic circuit includes a reference voltage generator. The reference voltage generator includes first and second candidate circuits, a selector circuit, and a third circuit. The method includes, with the first candidate circuit, generating a first candidate reference voltage, with the second candidate circuit, generating a second candidate reference voltage, with the selector circuit, selecting one of the first and second candidate reference voltages, and with the third circuit, receiving a power supply voltage based on the selected candidate reference voltage. 
     In some embodiments, the method also includes, with the first candidate circuit, causing the first candidate reference voltage to change by an first amount in response to changing a temperature from a first temperature value to a second temperature value, and, with the second candidate circuit, causing the second candidate reference voltage to change by an second amount in response to changing the temperature from the first temperature value to the second temperature value, where the first amount is greater than the second amount. 
     In some embodiments, at temperatures which are greater than a crossover temperature, the first candidate reference voltage is greater than the second candidate reference voltage, at temperatures which are less than the crossover temperature, the first candidate reference voltage is less than the second candidate reference voltage, and, at the crossover temperature, the first candidate reference voltage is equal to the second candidate reference voltage. 
     In some embodiments, the method also includes, with the selector circuit selecting a maximum of the first candidate reference voltage and the second candidate reference voltage. 
     In some embodiments, the method also includes, with the third circuit, receiving the selected candidate reference voltage. 
     In some embodiments, the method also includes, with the third circuit, receiving a level shifted version of the selected first or second candidate voltage. 
     In some embodiments, the method also includes, with a voltage regulator generating the power supply voltage for a digital circuit and an analog circuit. 
     In some embodiments, at temperatures which are greater than a crossover temperature, the first candidate reference voltage is greater than the second candidate reference voltage, at temperatures which are less than the crossover temperature, the first candidate reference voltage is less than the second candidate reference voltage, and, at the crossover temperature, the first candidate reference voltage is equal to the second candidate reference voltage. 
     In some embodiments, the electronic circuit is specified to function at a particular temperature value less than the crossover temperature, and the method further includes, with the first candidate circuit is configured to generate the first candidate reference voltage with a particular reference voltage value at the particular temperature, where the voltage regulator is configured to generate the power supply voltage with a particular power supply voltage value in response to receiving a voltage of the particular reference voltage value, and where the analog circuit is configured to not function with the particular power supply voltage value at the particular temperature. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         FIG. 1  is a schematic diagram illustrating a power distribution system for an electronic system. 
         FIG. 2A  is a schematic diagram of a voltage generator according to an embodiment. 
         FIG. 2B  is a graph schematically illustrating the relationship between the voltage at power supply node Vdd and temperature. 
         FIG. 3  is a schematic diagram of a voltage generator according to another embodiment. 
         FIG. 4  is a graph schematically illustrating the relationship between the voltage at power supply node Vdd and temperature. 
         FIG. 5  is a schematic illustration of a maximum circuit. 
         FIG. 6  is a schematic diagram of a voltage generator according to another embodiment. 
         FIG. 7  is a graph schematically illustrating the relationship between the voltage at power supply node Vdd and temperature. 
         FIG. 8  is a schematic illustration of a maximum circuit. 
     
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     Particular embodiments of the invention are illustrated herein in conjunction with the drawings. 
     Various details are set forth herein as they relate to certain embodiments. However, the invention can also be implemented in ways which are different from those described herein. Modifications can be made to the discussed embodiments by those skilled in the art without departing from the invention. Therefore, the invention is not limited to particular embodiments disclosed herein. 
       FIG. 1  is a schematic diagram illustrating a power distribution system for an electronic system  100 . System  100  includes bandgap reference voltage generator  110 , power supply voltage generator  120 , digital circuitry  130 , an analog circuitry  140 . 
     Bandgap voltage generator  110  may be any bandgap voltage generator. For example any bandgap voltage generator known to those of skill in the art may be used. Typically bandgap voltage generators generate reference voltages which vary with temperature according to the temperature variation of one or more bipolar junction transistors and one or more resistors. In alternative embodiments, other reference voltage generators may be used. 
     Power supply voltage generator  120  receives a reference voltage from bandgap voltage generator  110 , and generates a power supply voltage based on the received reference voltage. For example, power supply voltage generator  120  may receive a 1 V reference voltage from reference voltage generator  110 , and generate a 3 V supply voltage. 
     In some embodiments, power supply voltage generator  120  generates a supply voltage which is a substantially constant factor times the received reference voltage. For example, the supply voltage may be three times the received reference voltage. For example, if power supply voltage generator  120  receives a 1.1 V reference voltage from reference voltage generator  110 , power supply voltage generator  120  may generate a 3.3 V supply voltage. 
     In this embodiment, power supply voltage generator  120  comprises a DC-DC LDO (low dropout regulator). In alternative embodiments, other voltage regulators or voltage generators may be used. 
     Digital circuitry  130  receives the supply voltage generated by power supply voltage generator  120 , and operates according to the functionality of the digital circuitry therein, as powered by current received from the power supply voltage generator  120 . 
     Analog circuitry  140  receives the supply voltage generated by power supply voltage generator  120 , and operates according to the functionality of the analog circuitry therein, as powered by current received from the power supply voltage generator  120 . Analog circuitry  140  receives the supply voltage generated by power supply voltage generator  120 , and operates according to the functionality of the analog circuitry, as powered by current received from the power supply voltage generator  120 . 
     Bandgap reference voltage generator  110  may be advantageously configured to generate a reference voltage which varies with temperature. The requirements for the reference voltage generated by bandgap reference voltage generator  110  include that the generated reference voltage causes power supply voltage generator  120  generate a supply voltage which allows for digital circuitry  130  and analog circuitry  140  to operate within their respective specified functionality limits. 
     As understood by those of skill in the art, the functionality of each of digital circuitry  130  and analog circuitry  140  is affected by temperature. For example, each of digital circuitry  130  analog circuitry  140  may operate faster at colder temperatures. Therefore, bandgap reference voltage generator  110  may advantageously generate a lower reference voltage at a lower temperature because the resulting lower supply voltage is sufficient for the digital circuitry  130  and analog circuitry  140  to operate within their respective specified functionality limits. 
     As understood by those of skill in the art, analog circuitry  140  has power supply voltage requirements which are independent of speed. For example, analog circuitry  140  will have insufficient voltage headroom if the power supply voltage is too low, regardless of the analog circuitry  140  being fast enough at the low power supply voltage. 
       FIG. 2A  is a schematic diagram of a bandgap voltage reference generator  200  according to an embodiment. Bandgap voltage reference generator  200  may, for example, be used as bandgap reference voltage generator  110  in system  100  of  FIG. 1 . 
     Bandgap voltage reference generator  200  is shown only as an example. As is understood by those of skill in the art, there are many bandgap voltage reference generator topologies which may be used. As understood by those of skill in the art, the principles and aspects discussed herein may be applied with ordinary skill to alternative bandgap voltage reference generator topologies. 
     The basic functionality of bandgap voltage reference generator  200  is well understood the art, will be omitted for the sake of brevity. 
     Regarding bandgap voltage reference generator  200 , as understood by those of skill in the art, the voltage temperature coefficient of the voltage at node VC may be influenced by the value of variable resistor R 2 . Similarly, as understood by those of skill in the art, the voltage temperature coefficient of the voltage at node VP may be influenced by the value of variable resistor R 3 . 
     In this embodiment, controller  220  is configured to generate control voltages for variable resistors R 2  and R 3 . Based on results of calibration techniques understood by those of skill in the art, controller  220  generates the control voltages. 
     In the illustrated embodiment, controller  220  generates the control voltages such that the voltage at node VC either increases or decreases with increased temperature. For example, controller  220  may generate a control voltage for variable resistor R 2  such that the voltage at node VC decreases with increased temperature. 
     In the illustrated embodiment, controller  220  generates the control voltages such that the voltage at node VP increases with changing temperature. For example, controller  220  may generate a control voltage for variable resistor R 3  such that the voltage at node VP increases across temperature. 
     Maximum circuit  230  receives the voltages at nodes VC and VP, and generates a voltage at output node Vref which corresponds with the greater of the voltages at nodes VC and VP. For example, the voltage at node VC may be 1.1 V and the voltage at node VP may be 1 V. As a result, maximum circuit  230  may generate a voltage at output node Vref which is equal to 1.1 V. In some embodiments, the voltage generated by maximum circuit  230  at output node Vref may be a level shifted version of the greater of the voltages at nodes VC and VP. A non-limiting example of a maximum circuit is discussed below. Other maximum circuits understood by those of skill in the art may be used. 
     In this embodiment, at temperatures which are less than a crossover temperature, the voltage at node VP is greater than the voltage at node VC. Similarly, at temperatures which are greater than the crossover temperature, the voltage at node VC is greater than the voltage at node VP. At the crossover temperature, the voltage at node VP is equal to the voltage at node VC. As a result, at temperatures greater than the crossover temperature, the voltage at output node Vref (Vdd in  FIG. 2B ) is equal to or corresponds with the voltage at node VC, and at temperatures less than the crossover temperature, the voltage at output node Vref is equal to or corresponds with the voltage at node VP. 
     When used in systems, such as system  100  of  FIG. 1 , the voltage at power supply node Vdd has a temperature profile corresponding with or substantially identical to the voltage at reference node Vref. 
     At temperatures less than the crossover temperature, the voltage at output node Vref (Vdd in  FIG. 2B ) is equal to or corresponds with the voltage at node VP, and decreases in temperature cause the digital circuitry  130  and the analog circuitry  140  to slow down. However, the decreases in temperature also cause voltage at power supply node Vdd to increase. Therefore, the increased voltage at power supply node Vdd may advantageously compensate or at least partially compensate for the circuitry slowness, thereby extending the temperature range over which the digital circuitry  130  and the analog circuitry  140  operate according to their specified functionality. 
     Similarly, at temperatures less than the crossover temperature, increases in temperature cause the digital circuitry  130  and the analog circuitry  140  to speed up. However, the increases in temperature also cause voltage at power supply node Vdd to decrease. Therefore, the decreased voltage at the power supply node Vdd advantageously allows for the digital circuitry  130  and the analog circuitry  140  to operate according to their specified functionality using less power. 
     At temperatures greater than the crossover temperature, the voltage at output node Vref (Vdd in  FIG. 2B ) is equal to or corresponds with the voltage at node VC, and the voltage power supply node advantageously changes according to changes in the voltage at node VC. As a result, temperatures greater than the crossover temperature to not cause the voltage at power supply node Vdd to drop below that which would allow the analog circuitry  140  to operate properly. 
     Accordingly, the voltage-temperature profile slope−change in voltage/change in temperature (dv/dtemp) for the voltage at the power supply node Vdd for temperatures greater than the crossover temperature is determined by the dv/dtemp of the voltage at node VC, and is different from the dv/dtemp slope at temperatures less than crossover temperature, where the voltage at the power supply node Vdd is determined by the dv/dtemp of the voltage at node VP. 
     In some embodiments, the Vdd voltage dv/dtemp slope at temperatures greater than the crossover temperature is large enough that, if the Vdd voltage were to continue to drop for decreasing temperature with the same dv/dtemp slope for temperatures less than the crossover temperature, the analog or digital circuitry would fail at a temperature specified as allowing for functional operation. Similarly, in some embodiments, the Vdd voltage dv/dtemp slope at temperatures less than the crossover temperature is large enough that, if the Vdd voltage were to continue to drop for increasing temperature with the same dv/dtemp slope for temperatures greater than the crossover temperature, the analog or digital circuitry would fail at a temperature specified as allowing for functional operation. This is illustrated in  FIG. 2B . 
       FIG. 3  is a schematic diagram of a bandgap voltage reference generator  300  according to another embodiment. Bandgap voltage reference generator  300  may, for example, be used as bandgap reference voltage generator  110  in system  100  of  FIG. 1 . 
     Bandgap voltage reference generator  300  is shown only as an example. As is understood by those of skill in the art, there are many bandgap voltage reference generator topologies which may be used. As understood by those of skill in the art, the principles and aspects discussed herein may be applied with ordinary skill to alternative bandgap voltage reference generator topologies. 
     The basic functionality of bandgap voltage reference generator  300  is well understood the art, will be omitted for the sake of brevity. 
     Regarding bandgap voltage reference generator  300 , as understood by those of skill in the art, the temperature coefficient of the voltage at node VC may be influenced by the value of variable resistor R 3 . 
     In this embodiment, controller  320  is configured to generate control voltage for variable resistor R 3 . Based on results of calibration techniques understood by those of skill in the art, controller  320  generates the control voltage. In the illustrated embodiment, controller  320  generates the control voltage such that the voltage at node VC decreases with increasing temperature. 
     In addition, the reference generator  300  may be designed such that the voltage at node VT increases with increasing temperature. 
     Maximum circuit  330  receives the voltages at nodes VC and VT, and generates a voltage at output node Vref which corresponds with the greater of the voltages at nodes VC and VT. For example, the voltage at node VC may be 1.1 V and the voltage at node VT may be 1 V. As a result, maximum circuit  330  may generate a voltage at output node Vref which is equal to 1.1 V. In some embodiments, the voltage generated by maximum circuit  330  at output node Vref may be a level shifted version of the greater of the voltages at nodes VC and VT. A non-limiting example of a maximum circuit is discussed below. Other maximum circuits understood by those of skill in the art may be used. 
     In this embodiment, at temperatures which are less than a crossover temperature, the voltage at node VT is greater than the voltage at node VC. Similarly, at temperatures which are greater than the crossover temperature, the voltage VC is greater than the voltage at node VT. At the crossover temperature, the voltage at node VT is equal to the voltage at node VC. As a result, at temperatures greater than the crossover temperature, the voltage at output node Vref (Vdd in  FIG. 4 ) is equal to or corresponds with the voltage at node VC, and at temperatures less than the crossover temperature, the voltage at output node Vref is equal to or corresponds with the voltage at node VT. 
     When used in systems, such as system  100  of  FIG. 1 , the voltage at power supply node Vdd has a temperature profile corresponding with or substantially identical to the voltage at reference node Vref. 
     At temperatures less than the crossover temperature, the voltage at output node Vref (Vdd in  FIG. 4 ) is equal to or corresponds with the voltage at node VT, and decreases in temperature cause the digital circuitry  130  and the analog circuitry  140  to slow down. However, the decreases in temperature also cause voltage at power supply node Vdd to increase. Therefore, the increased voltage at power supply node Vdd may advantageously compensate or at least partially compensate for the circuitry slowness, thereby extending the temperature range over which the digital circuitry  130  and the analog circuitry  140  operate according to their specified functionality. 
     Similarly, at temperatures less than the crossover temperature, increases in temperature cause the digital circuitry  130  and the analog circuitry  140  to speed up. However, the increases in temperature also cause voltage at power supply node Vdd decrease. Therefore, the decreased voltage at the power supply node Vdd advantageously allows for the digital circuitry  130  and the analog circuitry  140  to operate according to their specified functionality using less power. 
     At temperatures greater than the crossover temperature, the voltage at output node Vref (Vdd in  FIG. 4 ) is equal to or corresponds with the voltage at node VC, and the voltage power supply node advantageously changes according to changes in the voltage at node VC. As a result, temperatures less than the crossover temperature do not cause the voltage at power supply node Vdd to drop below that which would allow the analog circuitry  140  to operate properly. 
     Accordingly, the voltage-temperature profile slope−change in voltage/change in temperature (dv/dtemp) for the voltage at the power supply node Vdd for temperatures greater than the crossover temperature is determined by the dv/dtemp of the voltage at node VC, and is different from the dv/dtemp slope at temperatures less than crossover temperature, where the voltage at the power supply node Vdd is determined by the dv/dtemp of the voltage at node VT. 
     In some embodiments, the Vdd voltage dv/dtemp slope at temperatures greater than the crossover temperature is large enough that, if the Vdd voltage were to continue to drop for decreasing temperature with the same dv/dtemp slope for temperatures less than the crossover temperature, the analog or digital circuitry would fail at a temperature specified as allowing for functional operation. Similarly, in some embodiments, the Vdd voltage dv/dtemp slope at temperatures less than the crossover temperature is large enough that, if the Vdd voltage were to continue to drop for increasing temperature with the same dv/dtemp slope for temperatures greater than the crossover temperature, the analog or digital circuitry would fail at a temperature specified as allowing for functional operation. This is illustrated in  FIG. 4 . 
       FIG. 4  is a graph schematically illustrating the relationship between the voltage at power supply node Vdd and temperature. 
     As shown, in this embodiment, for temperatures greater than the crossover temperature, the voltage at power supply node Vdd increases with increased temperature, and decreases with decreased temperature. In contrast, in this embodiment, for temperatures less than the crossover temperature, the voltage power supply node Vdd decreases with increased temperature, and increases with decreased temperature. 
       FIG. 4  also indicates a minimum Vdd voltage for proper functionality. Were the voltage at power supply node Vdd to decrease below this threshold, system  100  would not function properly. As shown, because the voltage at power supply node Vdd below the crossover temperature does not decrease with decreased temperature at the same rate as above the crossover temperature, the voltage at power supply node Vdd remains above the minimum for functional operation. Similarly, because the voltage at power supply node Vdd above the crossover temperature does not decrease with increased temperature at the same rate as below the crossover temperature, the voltage at power supply node Vdd remains above the minimum for functional operation. Accordingly, the system  100  maintains sufficient voltage at power supply node Vdd for high temperatures, and increases the voltage at power supply node Vdd for low temperatures, when the digital and analog circuitry operate slower. 
       FIG. 5  is a schematic illustration of a maximum circuit which may be used as a maximum circuit discussed elsewhere herein. 
     As shown, transistors M 5  and M 6  form a multiplexer, which electrically connects output node Vref to either of nodes VC and VT. Which of nodes VC and VT are electrically connected to output node Vref is determined by the differential gain circuit, as illustrated, and as understood by those of skill in the art. The differential gain circuit is configured to electrically connect node VC to output node Vref if the voltage at node VC is greater than the voltage node VT, and is configured to electrically connect node VT to output node Vref the voltage at node VT is greater than the voltage at node VC. In some embodiments, the differential gain circuit is hysteretic. 
       FIG. 6  is a schematic diagram of a bandgap voltage reference generator  600  according to another embodiment. Bandgap voltage reference generator  600  may, for example, be used as bandgap reference voltage generator  110  in system  100  of  FIG. 1 . 
     Bandgap voltage reference generator  600  is shown only as an example. As is understood by those of skill in the art, there are many bandgap voltage reference generator topologies which may be used. As understood by those of skill in the art, the principles and aspects discussed herein may be applied with ordinary skill to alternative bandgap voltage reference generator topologies. 
     The basic functionality of bandgap voltage reference generator  600  is well understood the art, will be omitted for the sake of brevity. 
     Regarding bandgap voltage reference generator  600 , as understood by those of skill in the art, the voltages and temperature coefficients of the voltages at nodes VP, VC, VTpVTn, and VBG are be influenced by the value of the variable resistors in the circuit. In this embodiment, controller  620  is configured to generate control voltages for the variable resistors. Based on results of calibration techniques understood by those of skill in the art, controller  620  generates the control voltages so as to cause the circuit to generate desired voltages and temperature coefficients of the voltages at nodes VP, VC, VTpVTn, and VBG. In the illustrated embodiment, controller  620  generates the control voltage such that the voltages at nodes VP, VC, VTpVTn, and VBG have the temperature profiles illustrated in  FIG. 7 . As understood by those of ordinary skill in the art, the voltages at nodes VP, VC, VTpVTn, and VBG may have voltage profiles other than that illustrated in  FIG. 7 . 
     Maximum circuit  630  receives the voltages at nodes VP+Vt, VC+Vt, VTpVTn+Vt, and VBG+Vt, and generates a voltage at output node Vref which corresponds with the greatest of voltages at nodes VP, VC, VTpVTn, and VBG. A non-limiting example of a maximum circuit is discussed below. Other maximum circuits understood by those of skill in the art may be used. 
     When used in systems, such as system  100  of  FIG. 1 , the voltage at power supply node Vdd has a temperature profile corresponding with or substantially identical to the voltage at reference node Vref. 
     Accordingly, the voltage-temperature profile slope—change in voltage/change in temperature (dv/dtemp) for the voltage at the power supply node Vdd is temperature dependent, and corresponds with the dv/dtemp temperature profile of a selected one of the voltages at nodes VP, VC, VTpVTn, and VBG of bandgap voltage reference generator  600 . 
       FIG. 7  is a graph schematically illustrating the relationship between the voltage at power supply node Vdd and temperature. 
     As shown, in this embodiment, the voltage at power supply node Vdd is equal to the greatest of the voltages at nodes VP, VC, VTpVTn, and VBG for all temperatures. Accordingly, the dv/dtemp temperature profile of Vdd is equal to the respective dv/dtemp temperature profile of the greatest of the voltages at nodes VP, VC, VTpVTn, and VBG for all temperatures. 
       FIG. 7  also indicates a minimum Vdd voltage for proper functionality. Were the voltage at power supply node Vdd to decrease below this threshold, system  100  would not function properly. As shown, because the voltage at power supply node Vdd is equal to the voltages at nodes VP, VC, VTpVTn, and VBG for all, the system  100  maintains sufficient voltage at power supply node Vdd for all temperatures. 
       FIG. 8  is a schematic illustration of a maximum circuit which may be used as a maximum circuit discussed elsewhere herein. 
     As understood by those of skill in the art, the voltage at output node Vref is equal to the greatest of the voltages at nodes VP+Vt, VC+Vt, VTpVTn+Vt, and VBG+Vt minus Vt. Accordingly, the voltage at the output node Vref is equal to the greatest of the at nodes VP, VC, VTpVTn, and VBG. 
     Though the present invention is disclosed by way of specific embodiments as described above, those embodiments are not intended to limit the present invention. Based on the methods and the technical aspects disclosed herein, variations and changes may be made to the presented embodiments by those of skill in the art without departing from the spirit and the scope of the present invention.