Patent Publication Number: US-2010128643-A1

Title: Wireless Transmission/Reception Apparatus and Wireless Transmission/Reception Method

Description:
CROSS REFERENCE TO RELATED APPLICATIONS 
     This application claims priority to and the benefit of Japan Patent Application No. 2006-294354 filed on Oct. 30, 2006, the entire contents of which are incorporated herein by reference. 
     TECHNICAL FIELD 
     The present invention relates to a wireless transmission/reception apparatus and a wireless transmission/reception method. 
     BACKGROUND ART 
     In a wireless communication environment, interference of fading caused by multipath and interference of delayed waves caused by time fluctuations of a propagation path environment due to the Doppler shift are the factors for deterioration of the quality of received signals. 
     As a wireless transmission/reception apparatus designed to improve such problem, for example, a configuration shown in  FIG. 6  is known. This wireless transmission/reception apparatus has a plurality of antennas  101 - 1 ˜ 101 - k  that constitute a multi-antenna, and performs antenna diversity both for transmission and reception, then transmits and receives data by using the Time Division Duplex (TDD) scheme and the multicarrier scheme of OFDMA (Orthogonal Frequency Division Multiple Access).  FIG. 6(   a ) shows a function block diagram of a receiver for the wireless transmission/reception apparatus, and  FIG. 6(   b ) shows a function block diagram of a transmitter for the wireless transmission/reception apparatus. 
     As for this wireless transmission/reception apparatus, in the receiver shown in  FIG. 6(   a ), the received signals at the antennas  101 - 1 ˜ 101 - k  are demodulated per subcarrier by using Fast Fourier Transform respectively by the corresponding FFT processing units  102 - 1 ˜ 102 - k , then subjected to frequency mapping by a logic mapping unit  103  and supplied to the burst processing units  104 - 1 ˜ 104 - k.    
     The burst processing units  104 - 1 ˜ 104 - k  have a reception weight calculation unit  105 - 1 , a received signal unit  106 - 1  and a decoder  107 - 1 . The received signals that have been subjected to frequency mapping by the logic mapping unit  103  are supplied in parallel to the reception weight calculation unit  105 - 1  and the received signal synthesizing unit  106 - 1 . Then in the reception weight calculation unit  105 - 1 , based on the received signal of a known signal (e.g. preamble) in a reception frame, a weight (weight vector) that allows each user (each channel) to obtain the maximum reception gain is calculated. In this case, the weight vector is calculated in accordance with the antenna diversity scheme by the antennas  101 - 1 ˜ 101 - k , for example, Adaptive Antenna System (AAS) and MIMO. 
     The weight vector calculated by the reception weight calculation unit  105 - 1  is supplied to the transmitter and the received signal synthesizing unit  106 - 1  as well. Then in the received signal synthesizing unit  106 - 1 , the weight vector is multiplied with respect to the received signal from the antennas  101 - 1 ˜ 101 - k . Thus the received signal is synthesized. The synthesized received signal is decoded by the decoder  107 - 1 . 
     In this manner, in the receiver, to the received signals from the antennas  101 - 1 ˜ 101 - k , reception process for weighting so as to obtain a high diversity gain by regulating fluctuations due to frequency selective fading is performed. 
     On the other hand, as shown in  FIG. 6(   b ), the transmitter has burst processing units  111 - 1 ˜ 111 - k , a physical mapping unit  112  and IFFT processing units  113 - 1 ˜ 113 - k . Then, an information signal to be transmitted is supplied to the burst processing units  111 - 1 ˜ 111 - k  and a weight vector is supplied from the burst processing units  104 - 1 ˜ 104 - k  of the receiver shown in  FIG. 6(   a ) as well. 
     The burst processing units  111 - 1 ˜ 111 - k  have an encoder  114 - 1  and a transmission weighting unit  115 - 1 . The information signal to be transmitted is coded by the encoder  114 - 1  and supplied to the transmission weighting unit  115 - 1 , where the information signal is mapped per subcarrier and demodulated. In addition, the weight vector from the receiver is supplied to the transmission weighting unit  115 - 1 . Then, based on the weight vector, the transmission information to the antennas  101 - 1 ˜ 101 - k  is weighted. The weighted transmission information is subjected to frequency mapping by the physical mapping unit  112  and supplied to the IFFT processing units  113 - 1 ˜ 113 - k , where the information is subjected to inverse Fast Fourier Transform and transmitted from the antennas  101 - 1 ˜ 101 - k.    
     In this manner, in the transmitter, by weighting and transmitting the transmission signal from the antennas  101 - 1 ˜ 101   k  in the next transmission frame based on the weight vector calculated on the receiver side, it is possible to obtain the highest synthesized gain on the receiver side. 
     However, the wireless transmission/reception apparatus shown in  FIG. 6  has effect on the fluctuations due to frequency selective fading, but does not compensate for the fluctuations of received signal due to temporal fading caused by a movement of a mobile terminal or the like. 
     As an apparatus that can compensate for the fluctuations due to temporal fading, for example, in Japanese Unexamined Patent Application Publication No. 2004-112098, a wireless transmission/reception apparatus that ensures the follow-up performance relative to the fluctuations due to temporal fading of propagation paths by storing some of the weights that have been calculated at the time of process during which reception has succeeded in the case of communication of data stream such as packet or the like, and by performing retransmission process by selecting a weight that maximizes an antenna diversity gain from the stored weights at the time of retransmission of the data that has caused reception error, is disclosed. 
     SUMMARY OF INVENTION 
     Technical Problem 
     However, the wireless transmission/reception apparatus disclosed in the above mentioned Japanese Unexamined Patent Application Publication No. 2004-112098, at the time of retransmission process of the data stream that has caused reception error, compensates for the fluctuations due to temporal fading by using the weights that have been calculated in the past. Therefore, it is not possible to quickly respond to the temporal fading. Because of this, particularly, it is not possible to follow the fluctuations due to high-speed temporal fading caused by a high-speed movement of a mobile terminal or the like. As a result of that, there is concern that a transmission process is performed frequently, causing reduction in a communication speed. 
     Therefore, an object of the present invention in view of such circumstances is to provide a reliable wireless transmission/reception apparatus and wireless transmission/reception method that can quickly follow the fluctuations due to high-speed temporal fading and can also perform communication at the time of a high-speed movement of a mobile terminal without reducing the communication speed of data. 
     Solution to Problem 
     According to a first aspect of the present invention to achieve the above object, a wireless transmission/reception apparatus having a plurality of antennas, performing antenna diversity for transmission and reception, and transmitting and receiving radio signal of a frame structure containing a plurality of symbol sequences in a frequency axis direction and a time axis direction by using a time division duplex scheme and a multicarrier scheme, comprising: 
     a reception weight calculation unit for calculating a weight based on a first known signal contained in the symbol sequences in the frequency axis direction among received signals obtained from the plurality of antennas; 
     a received signal synthesizing unit for weighing and synthesizing the received signals based on the weight calculated by the reception weight calculation unit; 
     a correction amount calculation unit for calculating a correction amount of the symbol sequences at least in the time axis direction based on a second known signal contained in the symbol sequences in the time axis direction among synthesized received signals that have been synthesized by the received signal synthesizing unit; and 
     a transmission weighting unit for weighting, after a transmission signal to be transmitted from the plurality of antennas is corrected based on the correction amount, the transmission signal based on the weight in a transmission frame next to a reception frame where the weight and the correction amount have been calculated. 
     According to a second aspect of the present invention, in the wireless transmission/reception apparatus according to the first aspect, the correction amount calculation unit calculates, as the correction amount, respective average values of phase shift amount and amplitude fluctuation amount in a data area of the reception frame where the weight has been calculated. 
     According to a third aspect of the present invention, in the wireless transmission/reception apparatus according to the second aspect, the transmission weighting unit provides a transmission initial phase by performing phase shift of the average value of the phase shift amount by a time from the central point of the data area on a time axis in the reception frame where the correction amount has been calculated to a head of the next transmission frame. 
     Further, according to a fourth aspect of the present invention to achieve the above object, a wireless transmission/reception apparatus having a plurality of antennas, performing antenna diversity for transmission and reception, and transmitting and receiving radio signal of a frame structure containing a plurality of symbol sequences in a frequency axis direction and a time axis direction by using a time division duplex scheme and a multicarrier scheme, comprising the steps of; 
     calculating a weight based on a first known signal contained in the symbol sequences in the frequency axis direction among received signals obtained from the plurality of antennas; 
     weighting and synthesizing the received signals based on the calculated weight; 
     calculating a correction amount of the symbol sequences at least in the time axis direction based on a second known signal contained in the symbol sequences in the time axis direction among synthesized received signals that have been synthesized; and 
     weighting, after correcting a transmission signal to be transmitted from the plurality of antennas based on the correction amount, the transmission signal based the weight in a transmission frame next to a reception frame where the weight and correction amount have been calculated. 
     According to a fifth aspect of the present invention to achieve the above object, the wireless transmission/reception apparatus according to the fourth aspect, further comprising the steps of; correcting the synthesized received signal based on the calculated correction amount; and recognizing error about the corrected synthesized received signal, wherein, when there is no error that cannot be corrected based on the recognition, the transmission signal to be transmitted from the plurality of antennas is corrected based on the correction amount and weighted based on the weight in the transmission frame next to the reception frame. 
     ADVANTAGEOUS EFFECT ON INVENTION 
     According to the present invention, a weight that maximizes a reception gain and a correction amount in the time axis direction are calculated in the reception frame, and based on these calculated weight and correction amount, a transmission signal to be transmitted is corrected and weighted in the next transmission frame. Therefore, it is possible to quickly follow the fluctuations due to high-speed temporal fading. Thus, a reliable wireless transmission/reception method and apparatus, that can perform communication without reducing a data communication speed even when a mobile terminal moves at a high speed, can be realized. 
    
    
     
       BRIEF DESCRIPTION OF DRAWINGS 
         FIG. 1  is a function block diagram showing a receiver and a transmitter of the wireless transmission/reception apparatus according to an embodiment of the present invention; 
         FIG. 2  is a diagram showing an example of a frame configuration for transmission and reception of the wireless transmission/reception apparatus shown in  FIG. 1 ; 
         FIG. 3  is a diagram schematically showing an application example of a weight vector and a linear correction amount of the wireless transmission/reception apparatus shown in  FIG. 1 ; 
         FIG. 4  is a flow chart showing a reception process by the receiver shown in  FIG. 1 ; 
         FIG. 5  is a flow chart showing a transmission process by the transmitter shown in  FIG. 1 ; and 
         FIG. 6  is a function block diagram showing a configuration of the receiver and the transmitter of the conventional wireless transmission/reception apparatus. 
     
    
    
     DESCRIPTION OF THE NUMBERS 
     
         
           1 - 1 ˜ 1 - k . Antenna 
           2 - 1 ˜ 2 - k . FFT processing unit 
           3 . Logic mapping unit 
           4 - 1 ˜ 4 - k . Burst processing unit 
           5 - 1 . Reception weight calculation unit 
           6 - 1 . Received signal synthesizing unit 
           7 - 1 . Linear correction unit 
           8 - 1 . Decoder 
           11 - 1 ˜ 11 - k . Burst processing unit 
           12 . Physical mapping unit 
           13 - 1 ˜ 13 - k . IFFT processing unit 
           14 - 1 . Encoder 
           15 - 1 . Transmission weighting unit 
       
    
     BEST MODE FOR CARRYING OUT THE INVENTION 
     Hereinafter, preferred embodiment of the present invention will now be described with reference to the accompanying drawings. 
       FIG. 1  shows a wireless transmission/reception apparatus according to an embodiment of the present invention.  FIG. 1(   a ) shows a function block diagram of a receiver and  FIG. 1(   b ) shows a function block diagram of a transmitter. This wireless transmission/reception apparatus is, as in the case of the wireless transmission/reception apparatus shown in  FIG. 6 , has a plurality of antennas  1 - 1 ˜ 1 - k  that constitute a multi-antenna, and performs antenna diversity both for transmission and reception and transmits and receives data by using the TDD (Time Division Duplex) scheme and the multicarrier scheme by the OFDMA (Orthogonal Frequency Division Multiple Access). In this case, for an explanatory convenience, the explanation is made assuming wireless transmission/reception apparatus is a base station. 
     As shown in  FIG. 1(   a ), the receiver has FFT processing units  2 - 1 ˜ 2 - k , a logic mapping unit  3  and burst processing units  4 - 1 ˜ 4 - k . The received signals at the antennas  1 - 1 ˜ 1 - k , after being subjected to Fast Fourier Transform and demodulated per subcarrier respectively by the corresponding FFT processing units  2 - 1 ˜ 2 - k , are subjected to frequency mapping by the logic mapping unit  3  and supplied to the burst processing units  4 - 1 ˜ 4 - k.    
     The burst processing units  4 - 1 ˜ 4 - k  have a reception weight calculation unit  5 - 1 , a received signal synthesizing unit  6 - 1 , a linear correction unit  7 - 1  and a decoder  8 - 1 . The received signals that have been subjected to frequency mapping by the logic mapping unit  3  are supplied in parallel to the reception weight calculation unit  5 - 1  and the received signal synthesizing unit  6 - 1 . The reception weight calculation unit  5 - 1  calculates, based on a received signal of a first known signal, a weight (weight vector) that allows each user (each channel) to obtain the maximum reception gain. 
     In the present embodiment, for example, as shown in  FIG. 2 , the wireless transmission/reception apparatus transmits and receives data by a frame structure that contains a plurality of symbol sequences in the frequency axis direction and the time axis direction. In other words, the wireless transmission/reception apparatus performs duplex communication by repeating an uplink frame UL-F (reception frame) and a downlink frame DL-F (transmission frame) alternately via a guard time Tg. In this case, the uplink frame UL-F and the downlink frame DL-F have a known preamble Pre contained in the symbol sequences in the frequency axis direction and a subsequent data area corresponding respectively to the terminals, and in the data area, a known pilot signal Pt (subcarrier), which is a reference signal for synchronization establishment, is included.  FIG. 2  shows a case where 1 channel consists of 18 subcarriers. 
     Therefore, in the present embodiment, the reception weight calculation unit  5 - 1  calculates, based on a received signal of the preamble Pre (a first known signal), a weight vector that allows each channel to obtain the maximum reception gain. In addition, the weight vector is calculated in accordance with the antenna diversity scheme for the antennas  1 - 1 ˜ 1 - k , for example, Adaptive Antenna System (AAS) and MIMO. 
     The weight vector calculated by the reception weight calculation unit  5 - 1  is supplied to the transmitter and also supplied to the received signal synthesizing unit  6 - 1 . The received signal synthesizing unit  6 - 1 , with respect to the all of the received signals (in the frequency axis direction and in the time axis direction) from the antennas  1 - 1 ˜ 1 - k , multiplies and synthesizes the weight vector and obtains a synthesized received signal. 
     In this case, any measures against the time fluctuations have not been taken to the synthesized received signal obtained from the received signal synthesizing unit  6 - 1 . Therefore, the synthesized received signal, as a sample time thereof becomes late, could have been subjected to phase shift and amplitude fluctuation due to the influence of fading. 
     Consequently, in the present embodiment, the synthesized received signal from the received signal synthesizing unit  6 - 1  is supplied to the linear correction unit  7 - 1 , where, based on a pilot signal Pt (a second known signal) contained in the synthesized received signal, respective average values of phase shift amount and amplitude fluctuation amount in the data area of the uplink frame UL-F are calculated as a linear correction amount in the time axis direction. Then, the linear correction unit  7 - 1  corrects the synthesized received signal based on the linear correction amount. At this time, since the weight is corrected per channel with respect to the frequency axis, the number of samples of linear average parameter is increased when the linear correction unit  7 - 1  takes a shift average of phase and amplitude of all of the pilot signals Pt within 1 channel. Then as a result, estimated errors of the linear correction amount can be reduced. 
     Therefore, when the linear correction unit  7 - 1  corrects the synthesized received signal by adding the linear correction amount of phase and amplitude to the synthesized received signal, reception errors can be reduced corresponding to the time fluctuations. In other words, generally, with respect to the communication with a mobile terminal (mobile station), incoming waves are subjected to the Doppler shift that is dependent on the Doppler frequency both for the mobile station and the base station. Because of this, the received signal will be in the state where amplitude and phase temporally fluctuate. In that case, in a short period of time such as a few μs, assuming that the fluctuation amount of a position vector of the mobile station and the base station is constant, it is possible to consider the fluctuations of phase and amplitude in the frame as linear by recognizing the Doppler fluctuation amount of the frame as a single amount. When such environment is assumed, when a symbol fluctuation from a frame head to a frame end is linearly interpolated, the influence of the Doppler fluctuation is reduced. Therefore, symbol errors (shift from the expected value) by phase and amplitude fluctuations at the rear portion of the frame can be reduced, and thus, the reception errors can be reduced. 
     The synthesized received signal corrected by the linear correction amount by the linear correction unit  7 - 1  is supplied to the decoder  8 - 1  and decoded. In addition, the linear correction amount calculated by the linear correction unit  7 - 1  is supplied to the transmitter. 
     On the other hand, as shown in  FIG. 1(   b ), the transmitter has burst processing units  11 - 1 ˜ 11 - k , a physical mapping unit  12  and IFFT processing units  13 - 1 ˜ 13 - k . To the burst processing units  11 - 1 ˜ 11 - k , an information signal to be transmitted is supplied and a weight vector and a linear correction amount from the burst processing units  4 - 1 ˜ 4 - k  of the receiver shown in  FIG. 1(   a ) are also supplied. 
     The burst processing units  11 - 1 ˜ 11 - k  has an encoder  14 - 1  and a transmission weighting unit  15 - 1 , and an information signal to be transmitted is coded by the encoder  14 - 1  and supplied to the transmission weighting unit  15 - 1 . The burst processing units  11 - 1 ˜ 11 - k  perform mapping of the information signal that has been coded by the encoder  14 - 1  per subcarrier and demodulate the signal. In addition, a weight vector and a linear correction amount from the receiver are supplied to the transmission weighting unit  15 - 1 . The transmission weighting unit  15 - 1 , based on these weight vector and linear correction amount, corrects and weights the information signal for transmitting to the antennas  1 - 1 ˜ 1 - k . The information signal, which has been corrected and weighted by the transmission weighting unit  15 - 1 , is subjected to frequency mapping by the physical mapping unit  12  and supplied to the IFFT processing units  13 - 1 ˜ 13 - k . The IFFT processing units  13 - 1 ˜ 13 - k  perform inverse Fast Fourier Transform on the information signal that has been subjected to frequency mapping by the physical mapping unit  12 , then the information signal that has been subjected to inverse Fast Fourier Transform is transmitted from the antennas  1 - 1 ˜ 1 - k.    
     In other words, an application example of the weight vector and the linear correction amount is schematically shown in  FIG. 3 . However, in this case, the transmitter immediately uses the linear correction amount determined by the receiver in the downlink frame DL-F, which is a transmission frame next to the uplink frame UL-F, which is a reception frame that has determined the linear correction amount. In other words, the transmitter, at first, performs linear interpolation of the time fluctuation of the propagation path by adding a phase fluctuation amount in the linear correction amount to the transmission signal that has been coded and mapped. In addition, the transmitter adds a weight vector as a transmission signal per antenna to the transmission signal that has been subjected to linear interpolation. After that, the transmitter transmits the signal to which the weight vector has been added. 
     In this case, a time difference as shown in  FIG. 3  exists between the transmission process and the reception process. Because of this, with respect to a phase (transmission initial phase) that is given to the first signal of the transmission signal, a phase shift amount (average value) is shifted by the amount of the time difference between the reception and the transmission of the communication system by taking the guard time Tg into consideration. Thus, a function that assists interpolation of time fluctuation of propagation path during transmission can be further expected. Therefore, in this case, the linear correction amount of the phase calculated by the uplink frame UL-F is an average value of the phase shift amount of the pilot signal Pt in the data area. Then, since the average value is located at the central point of the data area on the time axis, the transmission initial phase is given by performing phase shift of the calculated average phase shift amount by the amount of time from the central point to the head of the transmission portion that is defined with respect to the system. 
     In addition, the FFT processing units  2 - 1 ˜ 2 - k , the logic mapping unit  3 , and the burst processing units  4 - 1 ˜ 4 - k  that constitute the receiver and the burst processing units  11 - 1 ˜ 11 - k , the physical mapping unit  12  and the IFFT processing units  13 - 1 ˜ 13 - k  that constitute the transmitter are constituted by, for example, DSP (Digital Signal Processor) and FPGA (Field Programmable Gate Array). 
       FIGS. 4 and 5  are flow charts showing the reception process by the receiver and the transmission process by the transmitter of the wireless transmission/reception apparatus of the present embodiment. 
     At first, the reception process by the receiver shown in  FIG. 4  is concretely described. In the reception process, at first, the received signals at the antennas  1 - 1 ˜ 1 - k  are subjected to Fast Fourier Transform respectively by the FFT processing units  2 - 1 ˜ 2 - k . Then after that, the logic mapping unit  3  performs frequency mapping of the received signals that have been subjected to Fast Fourier Transform by the FFT processing units  2 - 1 ˜ 2 - k  (step S 1 ). Then, in each of the burst processing units  4 - 1 ˜ 4 - k , the reception weight calculation unit  5 - 1 , based on the received signals of the preamble Pre, calculates a weight vector that allows obtaining the maximum reception gain per channel (step S 2 ). The received signal synthesizing unit  6 - 1  multiplies and synthesizes the weight vector to the corresponding received signal and obtains a combined received signal (step S 3 ). 
     In other words, in step S 2 , at first, the reception weight calculation unit  5 - 1  calculates an error signal e(t) from the following equation (1), where an input signal is r(t), an output signal that has been demodulated is y(t), a weight vector is W, and an input signal sequence vector of each antenna is X(t), provided that when 0≦t&lt;N Pre , N Pre  indicates the number of preambles. 
       [Equation 1] 
         e ( t )= r ( t )− y ( t )= r ( t )− W   H   X ( t )  (1) 
     Next, the reception weight calculation unit  5 - 1  calculates, in accordance with the least square error method, an expected square value of the error signal from the following equation 2. 
       [Equation 2] 
       [| e ( t ) 2   |]=E[|r ( t )− W   H   X ( t )| 2 ]  (2) 
     Further, the reception weight calculation unit  5 - 1  differentiates and expands the above mentioned equation (2) to obtain the following equation (3). 
       [Equation 3] 
       ∇ wE└|e ( t )| 2 ┘=−2 r   xd +2 R   xx   W   (3) 
     Provided that r xd  indicates a correlation vector between a reference signal and an input signal, and R xx  indicates a correlation matrix between each of the antennas. 
     Based on the above mentioned equation (3), the reception weight calculation unit  5 - 1  calculates an optimal weight vector W opt  from the equation (4) shown below. 
       [Equation 4] 
         W   opt   =R   xx   −1   r   xd   (4) 
     Further, in step S 3 , the received signal synthesizing unit  6 - 1  determines an output signal y(t) after demodulation, which is a synthesized received signal, in accordance with the following equation (5) by using the weight vector W opt  determined from the above mentioned equation (4), provided that in the equation (5), when 0≦t&lt;N symbol , N symbol  indicates a total symbol. 
       [Equation 5] 
         y ( t )= W   opt   H   X ( t )  (5) 
     When the synthesized received signal y(t) is determined, then, the linear correction unit  7 - 1  determines a linear average of phase (argument) and amplitude shifts in the time axis direction by using a known pilot signal Pt (subcarrier) included in the data area (steps S 4  and S 5 ), and based on that, performs linear correction of the synthesized received signal (step S 6 ). For this, at first, based on the above mentioned equation (4), the optimal vector W pilot  of the pilot signal Pt portion after demodulation shown in  FIG. 2  is determined from the following equation (6), where r yp  indicates a correlation vector between a reference signal and a demodulation signal, and r yy  indicates a correlation vector of the demodulation signal. 
       [Equation 6] 
         W   pilot   =r   yy   −1   r   yp   (6) 
     Next, the linear correction unit  7 - 1  determines an argument (phase shift amount) θ of W pilot  from the following equation (7). 
       [Equation 7] 
       θ= arg ( W   pilot )  (7) 
     In addition, since the expected value is 1, an amplitude fluctuation amount Δ r  of W pilot  is calculated from the following equation (8). [Equation 8] 
       Δ r =1 −|W   pilot |  (8) 
     After that, the linear correction unit  7 - 1  equally divides the argument θ and the amplitude fluctuation amount Δ r  determined from the above mentioned equations (7) and (8) by the number of the pilot symbols N pilot  in 1 channel, and determines a linear average θ sym  of the phase shift amount and a linear average Δ sym  of the amplitude fluctuation amount per symbol. 
     
       
         
           
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                       θ 
                     
                     
                       N 
                       pilot 
                     
                   
                 
               
               
                 
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     As described above, when the linear correction unit  7 - 1  determines the linear average θ sym  of the phase shift amount and the linear average Δ sym  of the amplitude fluctuation amount, fluctuations of phase and amplitude are corrected in a total symbol space by giving the result to the data symbol space as a shift amount in step S 6 . 
     When the linear correction unit  7 - 1  performs linear correction of the fluctuations of phase and amplitude of the synthesized received signal in step S 6 , the corrected synthesized signal is decoded by the decoder  8 - 1  (step S 7 ). In the present embodiment, error check (CRC check or the like) of decoded data frame or packet or the like is further performed and reliability is determined (step S 8 ). As a result of that, when there is no error that cannot be corrected, it is determined that the reliability is high, and the weight vector and the linear correction amount calculated in the frame are stored (step S 9 ). The stored weight vector and linear correction amount are used for the transmission process by the transmitter in the next transmission frame. 
     On the other hand, when there is an error that cannot be corrected, it is determined that the reliability is low, and the weight vector and the linear correction amount calculated in the frame are rejected (step S 10 ). In this case, the weight vector and the linear correction amount calculated in the highly reliable latest reception frame that have already been stored are used for the transmission process by the transmitter in the next transmission frame. 
     The steps after step S 2  are repeated in step S 11  for the number of times equal to the number of bursts, and the reception process is finished. 
     Next, the transmission process by the transmitter shown in  FIG. 5  is concretely described. As for the transmitter, at first, in each of the burst processing units  11 - 1 ˜ 11 - k , an information signal to be transmitted is coded by the encoder  14 - 1  (step S 21 ), then the signal is mapped and copied for the number of antennas by the transmission weighting unit  15 - 1 , then subjected to linear shift (step S 22 ) and weighting (step S 23 ) based on the linear correction amount and the weight vector from the receiver. 
     In other words, in step S 22 , the phase fluctuation amount of the linear correction amount from the receiver is added to the transmission signal that have been coded and mapped. In this case, since the phase fluctuation average (argument) in the data area of the uplink frame UL-F is θ, the time fluctuation per symbol is determined from the above mentioned equation (9). Therefore, as shown in  FIG. 3 , the number of symbols N DL  in the time T DL  is approximated by the following equation, where the time from the central point of the data area of the uplink frame UL-F to the first transmission symbol of the downlink frame DL-F is T DL  and a 1 symbol interval is t symbol . 
     
       
         
           
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                     DL 
                   
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                       T 
                       DL 
                     
                     
                       t 
                       symbol 
                     
                   
                 
               
               
                 
                   ( 
                   11 
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     Based on the above mentioned equation (11), a shift amount of the transmission signal that has been temporally transitioned from the uplink frame UL-F is defined as 
       e iθ     sym     N     DL   .  [Equation 11] 
     Then, when the transmission signal vector that has been coded, mapped and copied for the number of antennas is defined as X tx , the transmission signal X shifted-tx  to which the phase fluctuation is added per symbol is determined from the following equation (12), provided that when 0≦t&lt;N DL-END , N DL-END  indicates a total transmission symbol of 1 channel of the downlink frame DL-F. 
       [Equation 12] 
         X   shifted     —     tx ( t )= X   tx ( t ) e   iθ     sym     (N     DL     +t)   (12) 
     Moreover, in step S 23 , a weighed transmission signal vector Z(t) is calculated from the following equation, where the transmission weight vector is W tx . 
       [Equation 13] 
         Z ( t )= W   tx   H   X   shifted     —     tx ( t )  (13) 
     After the steps following step S 21  are repeated for the number of times equal to the number of bursts, frequency mapping by the physical mapping unit  12  and inverse Fast Fourier Transform by the IFFT processing units  13 - 1 ˜ 13 - k  are performed in step S 25 . Then the signal that has been subjected to inverse Fast Fourier Transform is transmitted from the antennas  1 - 1 ˜ 1 - k . Thus the process is finished. 
     As described above, in the present embodiment, the receiver calculates a weight that maximizes a reception gain and a fluctuation average of phase and amplitude as a linear correction amount in the time axis direction in the uplink frame UL-F, and the transmitter corrects and weights a transmission signal to be transmitted based on these calculated weight and linear correction amount in the next downlink frame DL-F. Therefore, it is possible to quickly follow the fluctuations due to high-speed temporal fading. Thus, since it is possible to perform communication without reducing a communication speed of data even during a high-speed movement of a mobile terminal. Thus QoS and reliability of communication can be improved. 
     Further, this invention is not limited to the above mentioned embodiment, but various modifications or changes are available. For example, in the above embodiment, a wireless transmission/reception apparatus is described as a base station. However, it is possible to apply in the same manner to a mobile station (terminal) when it has a multi antenna and performs antenna diversity. In this case, at the terminal, the uplink frame is a transmission frame and the downlink frame is a reception frame. Therefore, contrary to the case of the base station, a weight that maximizes a reception gain and a fluctuation average of phase and amplitude as a linear correction amount in the time axis direction are calculated in the downlink frame. Then based on these calculated weight and linear correction amount, a transmission signal to be transmitted may be corrected and weighted in the next uplink frame. In addition, communication scheme by multicarrier is not limited to OFDMA, but the present invention can effectively applied also to the known multicarrier schemes such as OFDM (Orthogonal Frequency Division Multiplexing) and DMT (Discrete Multi-Tone).