Patent Publication Number: US-2020294443-A1

Title: Light-emitting device driving circuit

Description:
BACKGROUND 
     Field of Invention 
     The present disclosure relates to a light-emitting device driving circuit for compensating a threshold voltage shift of a driving transistor therein. 
     Description of Related Art 
     The statements in this section merely provide background information related to the present disclosure and do not necessarily constitute prior art. 
     In recent years, different types of displays such as a thin film transistor liquid crystal display (TFT-LCD) and a thin film transistor organic light-emitting display (TFT-OLED) become more common and available. Some types of novel displays also being actively investigated with research and development resources, such as a mini light-emitting diode (mini-LED) display and a micro light-emitting diode (μ-LED) display. Conventional circuits for driving pixels in these displays encounter a problem on a threshold voltage shift of a driving transistor for driving a light-emitting device in the circuits. 
     SUMMARY 
     According to some embodiments of the present disclosure, a light-emitting device driving circuit including a light emitting device, a delivery capacitor, a driving transistor, a reset circuit, a compensation circuit, and a data circuit is provided. The delivery capacitor is electrically connected to a low-level voltage. The driving transistor is configured to drive the light-emitting device according to a driving voltage. The driving voltage is received from a driving voltage line in which a voltage level thereof is higher than that of the low-level voltage. The reset circuit is electrically connected to the driving transistor through a first node and is electrically connected to the light-emitting diode. The reset circuit is configured to determine whether to allow a current to flow from the first node to the low-level voltage through the light-emitting device. The compensation circuit is electrically connected to the first node and the delivery capacitor. The compensation circuit is configured to receive a reference voltage which is higher than the low-level voltage and to control a gate voltage of the driving transistor through a second node. The data circuit is configured to receive a data voltage and to determine whether to electrically connect the data voltage to the compensation circuit and whether to electrically connect the data voltage to the delivery capacitor. 
     It is to be understood that both the foregoing general description and the following detailed description are by examples, and are intended to provide further explanation of the disclosure as claimed. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       The disclosure can be more fully understood by reading the following detailed description of the embodiment, with reference made to the accompanying drawings as follows: 
         FIG. 1  is a schematic diagram of a light-emitting device driving circuit according to some embodiments of the present disclosure; 
         FIG. 2A  is a timing diagram of an operation for the light-emitting device driving circuit according to some embodiments of the present disclosure; 
         FIG. 2B  is a timing diagram of an operation for the light-emitting device driving circuit according to some embodiments of the present disclosure; 
         FIG. 2C  is a timing diagram of an operation for the light-emitting device driving circuit according to some embodiments of the present disclosure; 
         FIG. 2D  is a timing diagram of an operation for the light-emitting device driving circuit according to some embodiments of the present disclosure; 
         FIG. 2E  is a timing diagram of an operation for the light-emitting device driving circuit according to some embodiments of the present disclosure; 
         FIG. 2F  is a timing diagram of a combination of operations for the light-emitting device driving circuit according to some embodiments of the present disclosure; 
         FIG. 3A  is a schematic diagram of a light-emitting device driving circuit according to some embodiments of the present disclosure; 
         FIG. 3B  is a schematic diagram of a reset circuit according to some embodiments of the present disclosure; 
         FIG. 3C  is a schematic diagram of a compensation circuit according to some embodiments of the present disclosure; 
         FIG. 3D  is a schematic diagram of a data circuit according to some embodiments of the present disclosure; 
         FIG. 4A  is a light-emitting device driving circuit operated during the reset segment according to some embodiments of the present disclosure; 
         FIG. 4B  is a light-emitting device driving circuit operated during the compensation segment according to some embodiments of the present disclosure; 
         FIG. 4C  is a light-emitting device driving circuit operated during the data input segment according to some embodiments of the present disclosure; 
         FIG. 4D  is a light-emitting device driving circuit operated during the emission segment according to some embodiments of the present disclosure; 
         FIG. 5  is a schematic diagram of a light-emitting device driving circuit according to some embodiments of the present disclosure; 
         FIG. 6A  is a schematic diagram of a light-emitting device driving circuit according to some embodiments of the present disclosure; 
         FIG. 6B  is a schematic diagram of a reset circuit according to some embodiments of the present disclosure; 
         FIG. 6C  is a timing diagram of an operation for the light-emitting device driving circuit according to some embodiments of the present disclosure; 
         FIG. 7A  is the light-emitting device driving circuit operated during the reset segment according to some embodiments of the present disclosure; 
         FIG. 7B  is the light-emitting device driving circuit operated during the compensation segment according to some embodiments of the present disclosure; 
         FIG. 7C  is the light-emitting device driving circuit operated during the data input segment according to some embodiments of the present disclosure; 
         FIG. 7D  is the light-emitting device driving circuit operated during the emission segment according to some embodiments of the present disclosure; and 
         FIG. 8  is a schematic diagram of a light-emitting device driving circuit according to some embodiments of the present disclosure. 
     
    
    
     DETAILED DESCRIPTION 
     Reference will now be made in detail to the present embodiments of the disclosure, examples of which are illustrated in the accompanying drawings. Wherever possible, the same reference numbers are used in the drawings and the description to refer to the same or like parts. 
     In various embodiments, description is made with reference to figures. However, certain embodiments may be practiced without one or more of these specific details, or in combination with other known methods and configurations. In the following description, numerous specific details are set forth, such as specific configurations, dimensions, and processes, etc., in order to provide a thorough understanding of the present disclosure. In other instances, well-known semiconductor processes and manufacturing techniques have not been described in particular detail in order to not unnecessarily obscure the present disclosure. Reference throughout this specification to “one embodiment,” “an embodiment”, “some embodiments” or the like means that a particular feature, structure, configuration, or characteristic described in connection with the embodiment is included in at least one embodiment of the disclosure. Thus, the appearances of the phrase “in one embodiment,” “in an embodiment”, “according to some embodiments” or the like in various places throughout this specification are not necessarily referring to the same embodiment of the disclosure. Furthermore, the particular features, structures, configurations, or characteristics may be combined in any suitable manner in one or more embodiments. Although most of terms described in the following disclosure use singular nouns, said terms may also be plural in accordance with figures or practical applications. 
     Reference is made to  FIG. 1 .  FIG. 1  is a schematic diagram of a light-emitting device driving circuit  1000  according to some embodiments of the present disclosure. In some embodiments, a light-emitting device driving circuit  1000  including a light emitting device  100 , a delivery capacitor Cd, a driving transistor DT, a reset circuit  200 , a compensation circuit  300 , and a data circuit  400  is provided. The delivery capacitor Cd is electrically connected to a low-level voltage VSS. The driving transistor DT is configured to drive the light-emitting device  100  according to a driving voltage VDD. The driving voltage VDD is received by a driving voltage line LH and is electrically connected to the driving transistor DT. A voltage level of the driving voltage VDD is higher than a voltage level of the low-level voltage VSS. The low-level voltage VSS can be a ground level voltage, but should not be limited thereto. The driving voltage VDD can be provided by a power source circuit and will not be described herein in detail. The reset circuit  200  is electrically connected to the driving transistor DT through a first node N 1 . The reset circuit  200  is also electrically connected to the light-emitting device  100 . The reset circuit  200  is configured to determine whether to electrically connect the light-emitting device  100  to the first node N 1 . The compensation circuit  300  is electrically connected to the first node N 1  and the delivery capacitor Cd. The compensation circuit  300  is configured to receive a reference voltage Vref and to control a gate voltage of the driving transistor DT through a second node N 2 . A voltage level of the reference voltage Vref is higher than the voltage level of the low-level voltage VSS. In some embodiments, the reference voltage Vref and the driving voltage VDD can have the same voltage level (e.g., the driving voltage VDD is applied to the compensation circuit  300 ). The data circuit  400  is configured to receive a data voltage Vdata and to determine whether to electrically connect the data voltage Vdata to the compensation circuit  300  and whether to electrically connect the data voltage Vdata to the delivery capacitor Cd. 
     Although the “electrically connected” as interpreted in figures of the present disclosure is mainly for “direct connected, however, some minor electronic components (e.g., resistors) which do not affect operations and result as disclosed in the embodiments of the present disclosure can be present between two electrically connected components. They can be incorporated into the scope of the present disclosure. 
     In some embodiments, the reset circuit  200  includes two terminals T 1  and T 2  and a control terminal C 1 , but should not be limited thereto. In some embodiments, the compensation circuit  300  includes four terminals T 3 , T 4 , T 5 , and T 6  and two control terminals C 4  and C 5 , but should not be limited thereto. In some embodiments, the data circuit  400  includes two terminals T 7  and T 8  and a control terminal C 2 , but should not be limited thereto. 
     Reference is made to the reset circuit  200  as shown in  FIG. 1 . The terminal T 1  is electrically connected to a source terminal of the driving transistor DT through a first node N 1 . The terminal T 2  is electrically connected to the low-level voltage VSS via the light-emitting device  100 . The reset circuit  200  is electrically connected to the light-emitting device  100  in series between the driving transistor DT and the low-level voltage line LL. The determination of whether to electrically connect the first node N 1  to the light-emitting device  100  is in accordance with a scan signal SC 1  received by the control terminal C 1 . When the light-emitting device  100  and the driving transistor DT are electrically connected, they are electrically connected through the reset circuit  200 . 
     Reference is made to the compensation circuit  300  as shown in  FIG. 1 . The terminal T 3  is configured to receive the reference voltage Vref. The terminal T 4  is electrically connected to the driving transistor DT and is used to control a gate voltage of the driving transistor DT. The terminal T 5  is electrically connected to the reset circuit  200  through the first node (N 1 ). The terminal T 6  is electrically connected to one end of the delivery capacitor Cd different from another end of the delivery capacitor Cd which is electrically connected to the low-level voltage VSS. The compensation circuit  300  is configured to determine whether to receive the reference voltage Vref in accordance with a scan signal SC 4  received by the control terminal C 4 . The compensation circuit  300  is configured to determine whether to electrically connect the data circuit  400  and the delivery capacitor Cd to the first node N 1  in accordance with a scan signal SC 5  received by the control terminal C 5 . 
     Reference is made to the data circuit  400  as shown in  FIG. 1 . The terminal T 8  is electrically connected (e.g., directly connected, but should not be limited thereto) to the terminal T 6  of the compensation circuit  300 . The determination of whether to electrically connect the data voltage Vdata to the compensation circuit  300  and whether to electrically connect the data voltage Vdata to the delivery capacitor Cd is in accordance with a scan signal SC 2  received by the control terminal C 2 . 
     Reference is made to  FIG. 1  and  FIGS. 2A to 2E .  FIGS. 2A to 2E  are timing diagrams of operations for the light-emitting device driving circuit  1000  according to some embodiments of the present disclosure. The light-emitting device driving circuit  1000  is operated in a pre-emission time segment PETS and an emission time segment ES. The pre-emission time segment PETS does not overlap with the emission time segment ES. In some embodiments, the pre-emission time segment PETS includes a combination of a blank segment BS, a reset segment RS, a compensation segment CS, and a data input segment DIS (as referred to  FIG. 2A ). In some embodiments, the pre-emission time segment PETS includes a combination of the reset segment RS, the compensation segment CS, and the data input segment DIS. In some embodiments, the pre-emission time segment PETS includes a combination of a recovery segment RCS, the reset segment RS, the compensation segment CS, and a data input segment DIS (as referred to  FIGS. 2B and 2C ). In some embodiments, the pre-emission time segment PETS includes a combination of the recovery segment RCS, the blank segment BS, and the data input segment DIS (as referred to  FIG. 2D ). In some embodiments, the pre-emission time segment PETS includes a combination of the blank segment BS, the recovery segment RCS, the reset segment RS, the compensation segment CS, and the data input segment DIS. In some embodiments, the pre-emission time segment PETS includes a combination of the blank segment BS and the data input segment DIS (as referred to  FIG. 2E ). In some embodiments, the reset segment RS, the compensation segment CS, and the data input segment DIS are operated in sequence. Some of these different ways of operation are shown in  FIGS. 2A to 2E  as exemplifications. 
     Reference is made to  FIG. 2A , in which the light-emitting device driving circuit  1000  is operated in the pre-emission time segment PETS and the emission time segment ES, and the pre-emission time segment PETS includes the combination of the blank segment BS, the reset segment RS, the compensation segment CS, and the data input segment DIS. 
     An operation during the reset segment RS is as follows. The data circuit  400  is disabled and the reset circuit  200  and the compensation circuit  300  are enabled, such that the data voltage Vdata is disallowed to be applied to the driving transistor DT and a voltage difference between the second node N 2  and the first node N 1  is greater than a threshold voltage Vth of the driving transistor DT. Specifically, the scan signal SC 4  is applied to the control terminal C 4  of the compensation circuit  300  to enable a control of the gate voltage of the driving transistor DT by the reference voltage Vref. More precisely, the reference voltage Vref is applied to the driving transistor DT via the terminals T 3  and T 4  of the compensation circuit  300 . A voltage level of the reference voltage Vref is higher than a sum of voltage levels of a threshold voltage Vth of the driving transistor DT and the low-level voltage VSS so as to enable the driving transistor DT. Therefore, the driving voltage VDD is applied to drive a current to flow from the driving voltage line LH to a low-level voltage line LL via the first node N 1 . As a result, a voltage difference between the second node N 2  and the first node N 1  is increased and a voltage difference between the first node N 1  and the low-level voltage VSS becomes a voltage difference between two ends of the light-emitting device  100 . The dotted points present in some of the segments as illustrated in all of the timing diagrams means that a state of “enable” or “disable” is irrelevant during the segment under consideration. For example, the state of the scan signals SC 2 , SC 4 , and SC 5  are irrelevant during the blank segment BS, and only the scan signal SC 1  is applied to disable the reset circuit  200  during the blank segment BS in the embodiments as illustrated by  FIG. 2A . 
     The “enabled” and “disabled” described in the present disclosure are explained as follows. The reset circuit  200  is enabled (disabled) when a current is allowed (disallowed) to flow through the reset circuit  200 . The compensation circuit  300  is enabled when currents are allowed to flow through the terminals T 3  and T 6  and currents are allowed to flow through the terminals T 4  and T 5 . The compensation circuit  300  is disabled when a current is disallowed to flow through the terminal T 3  and a current is disallowed to flow through the terminal T 5 . In the reset segment RS, the terminal T 5  of the compensation circuit  300  can be optionally chosen to disallow a current to flow through thereof. A current is allowed to flow through the terminal T 6  when the compensation circuit  300  is disabled, and a current is allowed to flow through the terminal T 4  when the compensation circuit  300  is disabled. The data circuit  400  is enabled (disabled) when a current is allowed (disallowed) to flow through the terminal T 7  and through the terminal T 8 . 
     After the reset segment RS, the operation continues to the compensation segment CS. The operation during the compensation segment CS is as follows. The data circuit  400  and the reset circuit  200  are disabled and the compensation circuit  300  is enabled, such that a voltage level of the first node N 1  is gradually increased until a voltage difference between the second node N 2  and the first node (N 1 ) approaches the threshold voltage Vth of the driving transistor DT. That is, a gate-to-source voltage Vgs is substantially equal to the threshold voltage Vth of the driving transistor DT. Specifically, the voltage level of the first node N 1  is increased since a current flowing from the driving voltage line LH is disallowed to flow to the low-level voltage line LL, and the first node N 1  is substantially floated and electrically isolated from the low-level voltage VSS. Instead, the current flows to the terminal T 5  of the compensation circuit  300  via the first node N 1 , such that the floated first node N 1  is gradually charged to increase the voltage level of the first node N 1  until there is not enough electrical potential to drive said current, which is a moment when the gate-to-source voltage Vgs is substantially equal to the threshold voltage Vth of the driving transistor DT. A voltage difference substantially (acceptably) equal to the threshold voltage Vth of the driving transistor DT is thus stored in an electronic component (e.g., a capacitor, or the like) of the compensation circuit  300 . The term “substantially equal to” or “acceptably equal to” means close to a designated value (e.g., close to the threshold voltage) such that one can regard it as the designated value. 
     After the compensation segment CS, the operation continues to the data input segment DIS. The operation during the data input segment DIS is as follows. The reset circuit  200  and the compensation circuit  300  are disabled and the data circuit  400  is enabled, such that the data voltage Vdata and the threshold voltage Vth of the driving transistor DT stored in electronic components (e.g., capacitors, or the like) of the compensation circuit  300  are combined and applied to the driving transistor DT through the delivery capacitor Cd and the compensation circuit  300 . Specifically, the data voltage Vdata is applied to the terminal T 6  of the compensation circuit  300 , and the data voltage Vdata plus the threshold voltage Vth are combined by the compensation circuit ( 300 ) to control the gate voltage of the driving transistor DT in the next coming emission segment ES. As a result, the threshold voltage Vth of the driving circuit DT is substantially compensated. 
     After the data input segment DIS, the operation continues to the emission segment ES. The operation during the emission segment ES is as follows. The data circuit  400  and the compensation circuit  300  are disabled and the reset circuit  200  is enabled, such that the light-emitting device  100  is driven according to the driving voltage VDD and the gate voltage (which is equal to the data voltage Vdata plus the threshold voltage Vth of the driving transistor DT stored in electronic components (e.g., capacitors, or the like) of the compensation circuit  300 ) applied to the driving transistor DT via the compensation circuit  300 . 
     With the light-emitting device driving circuit  1000  and the operations described above, a threshold voltage shift of the driving transistor DT can be compensated and will not affect an emission current Id of the light-emitting device  100 . Specifically, after the operation of the data input segment DIS, the equation I: Vdata+Vth=Vgs+Von is satisfied, in which Von is a voltage difference between two ends of the light-emitting device  100  when the light-emitting device  100  is turned on with the emission current Id flowing through thereof driven by the driving transistor DT. A voltage sum of “Vdata+Vth” on the left-hand side of the equation I is measured between the second node N 2  and the low-level voltage VSS which is electrically connected to one end of the delivery capacitor Cd. A voltage sum of “Vgs+Von” on the right-hand side of the equation I is measured between the second node N 2  and the low-level voltage VSS which is electrically connected to one end of the light-emitting device  100 . Using the equation I, the emission current Id during the emission segment ES can be obtained by an algebra in the equation II: Id=K*(Vgs−Vth) 2 =K*(Vdata+Vth−Von−Vth) 2 =K*(Vdata−Von) 2 , which is independent of Vth, and K is a constant value related to properties of the driving transistor DT. The equation II is an exemplification under a first-order approximation which omits higher-order terms and under an assumption that the driving transistor DT is operated in the saturation region. However, the emission current Id and the threshold voltage Vth are also independent from each other when the driving transistors are operated in a linear region. 
     Another advantage of the light-emitting device driving circuit  1000  and the operations described above is to enhance a precision of controlling brightness, which is particularly useful in a low grayscale region of the light-emitting device  100 . Specifically, the emission current Id of the light-emitting device  100  is proportional to a voltage difference between two ends of the light-emitting device  100  (i.e., Von), and a drain-to-source current of the driving transistor DT (e.g., the thin film transistor in the present embodiments) is proportional to the gate-to-source voltage Vgs under a configuration of the light-emitting device driving circuit  1000 . As such, there are two voltage parameters: the voltage difference between two ends of the light-emitting device  100  (i.e., Von) and the gate-to-source voltage Vgs of the driving transistor DT) which can be used to control the brightness of the light-emitting device  100 , and these two voltage parameters (i.e., Von and Vgs) can be controlled by one voltage parameter Vdata according to the equation I: Vdata+Vth=Vgs+Von, derived above. Therefore, a data voltage difference ΔVdata corresponding to a given emission current difference ΔId in the above embodiments is greater than a gate-to-source voltage difference ΔVgs corresponding to said given emission current difference ΔId in conventional circuits, which substantially increases the precision of said control. 
     Yet another advantage of the light-emitting device driving circuit  1000  and the operations described above is that since the data circuit  400  is only enabled by the scan signal SC 2  during the data input segment DIS, the data voltage Vdata can be used to drive other pixels in other scan lines during the reset segment RS and the compensation segment CS of the pixel under consideration of the present embodiments, which greatly enhances a resolution, so that the data voltage Vdata is only occupied by one scan line time (i.e. only occupied by the data input segment DIS) and can be used to drive high resolution display. The operations described above can substantially skip the duration for waiting the compensation segment CS, so as to be more suitable to drive a high resolution display. 
     Reference is made to  FIG. 2B . The difference between embodiments as shown in  FIG. 2B  and the embodiments as shown in  FIG. 2A  is that the blank segment BS in the embodiments illustrated by  FIG. 2A  is replaced by the recovery segment RCS in the embodiments illustrated  FIG. 2B . In some embodiments, a combination of enablement and disablement of the reset circuit  200 , the compensation circuit  300 , and the data circuit  400  of the recovery segment RCS can be the same as that during the reset segment RS. The difference between the recovery segment RCS and the reset segment RS is that the voltage level of the reference voltage Vref applied during the reset segment RS is higher than a sum of the voltage levels of the threshold voltage Vth of the driving transistor DT, the low-level voltage VSS, and a voltage difference between two ends of the light-emitting device  100 , whereas a voltage level of the reference voltage Vref applied during the recovery segment RCS is lower than the sum of the voltage levels of the threshold voltage Vth of the driving transistor DT, the low-level voltage VSS, and the voltage difference between two ends of the light-emitting device  100 . Therefore, the threshold voltage shift of the driving transistor DT due to the operation during the emission segment ES may have a certain degree of recovery during the recovery segment RCS. 
     Reference is made to  FIG. 2C . The difference between embodiments as shown in  FIG. 2C  and the embodiments as shown in  FIG. 2B  is that the gate voltage of the driving transistor DT for said recovery is applied by the data voltage Vdata. A combination of enablement and disablement of the reset circuit  200 , the compensation circuit  300 , and the data circuit  400  during the recovery segment RCS in the embodiments illustrated by  FIG. 2C  can be the same as that during the data input segment DIS, except that a voltage level of the data voltage Vdata during the recovery segment RCS is lower than the sum of the voltage levels of the threshold voltage Vth of the driving transistor DT, the low-level voltage VSS, and the voltage difference between two ends of the light-emitting device  100 . 
     Reference is made to  FIG. 2D . The difference between embodiments as shown in  FIG. 2D  and the embodiments as shown in  FIG. 2C  is that the pre-emission time segment PETS in  FIG. 2D  includes only the recovery segment RCS, the blank segment BS, and the data input segment DIS. The reset segment RS and the compensation segment CS are not included in the pre-emission time segment PETS. It can be understood that not every frame needs compensation within one pixel. 
     Reference is made to  FIG. 2E . In some embodiments, the pre-emission time segment PETS only includes the blank segment BS and the data input segment DIS, in which the compensation circuit  300  and the data circuit  400  can be kept in states the same as those at the end of the previous operation, no matter they are enabled or disabled, while the reset circuit  200  is disabled. 
     Reference is made to  FIG. 2F .  FIG. 2F  is a timing diagram of a combination of operations for the light-emitting device driving circuit  1000  according to some embodiments of the present disclosure. Embodiments illustrated by  FIG. 2F  exemplifies a combination of four pre-emission time segments PETS and four emission time segments ES operated in sequence. The first pre-emission time segment PETS includes the blank segment BS and the data input segment DIS. The second pre-emission time segment PETS includes the blank segment BS, the reset segment RS, the compensation segment CS, and the data input segment DIS. The third pre-emission time segment PETS includes the recovery segment RCS, the reset segment RS, the compensation segment CS, and the data input segment DIS. The fourth pre-emission time segment PETS includes the recovery segment RCS, the blank segment BS, and the data input segment DIS. Although the embodiments illustrated by  FIG. 2F  only shows one example of the combination, it should not be limited thereto. Other embodiments with different type of combinations using the blank segment BS, the recovery segment RCS, the reset segment RS, the compensation segment CS, and the data input segment DIS are also within the scope of the present disclosure. 
     Reference is made to  FIGS. 3A to 3D  and  FIGS. 4A to 4D .  FIG. 3A  is a schematic diagram of a light-emitting device driving circuit  1000 - 1  according to some embodiments of the present disclosure.  FIG. 3B  is a schematic diagram of a reset circuit  200  according to some embodiments of the present disclosure.  FIG. 3C  is a schematic diagram of a compensation circuit  300  according to some embodiments of the present disclosure.  FIG. 3D  is a schematic diagram of a data circuit  400  according to some embodiments of the present disclosure.  FIG. 4A  is a schematic diagram of the light-emitting device driving circuit  1000 - 1  operated during the reset segment RS according to some embodiments of the present disclosure.  FIG. 4B  is a schematic diagram of the light-emitting device driving circuit  1000 - 1  operated during the compensation segment CS according to some embodiments of the present disclosure.  FIG. 4C  is a schematic diagram of the light-emitting device driving circuit  1000 - 1  operated during the data input segment DIS according to some embodiments of the present disclosure. The word “on/off” for the scan signal SC 1  and the word “off/on” for the scan signal SC 5  means that besides the embodiments in which the switching transistor  202  and the switching transistor  304  are disabled, there are also other two permissible embodiments. The first embodiment is that the switching transistor  202  is enabled while the switching transistor  304  is disabled. The second embodiment is that the witching transistor  202  is disabled while the switching transistor  304  is enabled.  FIG. 4D  is a schematic diagram of the light-emitting device driving circuit  1000 - 1  operated during the emission segment ES according to some embodiments of the present disclosure. The dotted lines drawn for some of the switching transistors in  FIGS. 4A to 4D  represent disabled switching transistors, and solid lines drawn for some of the switching transistors in  FIGS. 4A to 4D  represent enabled switching transistors. 
     In some embodiments, the reset circuit  200  includes a switching transistor  202 . The switching transistor  202  has terminals T 9  and T 10 , and a control terminal C 3  (referred to  FIG. 3B ). The terminal T 9  is electrically connected to the driving transistor DT through the first node N 1 , and the second terminal T 10  is electrically connected to the light-emitting device  100 . The control terminal C 3  is configured to receive the scan signal SC 1 . In some embodiments, the terminal T 9  of the switching transistor  202  serves as the terminal T 1  of the reset circuit  200 , the terminal T 10  of the switching transistor  202  serves as the terminal T 2  of the reset circuit  200 , and the control terminal C 3  of the switching transistor  202  serves as the control terminal C 1  of the reset circuit  200 . During the reset segment RS and the emission segment ES, the switching transistor  202  is enabled by the scan signal SC 1  to allow a current to flow from the first node N 1  to the low-level voltage line LL through the light-emitting device  100 . During the compensation segment CS, the switching transistor  202  is disabled by the scan signal SC 1 , and there is substantially no current flowing through the light-emitting device  100 . During the recovery segment RCS which uses the reference voltage Vref to recover the threshold voltage shift of the driving transistor DT, the switching transistor  202  is enabled by the scan signal SC 1 , and during the recovery segment RCS which uses the data voltage Vdata to recover the threshold voltage shift of the driving transistor DT, the switching transistor  202  is also disabled by the scan signal SC 1 . 
     In some embodiments, the compensation circuit  300  includes a storage capacitor Cst, a switching transistor  302 , and a switching transistor  304  (referred to  FIG. 3C ). The storage capacitor Cst has a first end e 1  and a second end e 2 . The switching transistor  302  has terminals T 15  and T 16 , and a control terminal C 6 . The terminal T 15  is electrically connected to the reference voltage Vref. The terminal T 16  is electrically connected to the first end e 1  of the storage capacitor Cst and the second node N 2 . The control terminal C 6  is configured receive the scan signal SC 4 . The switching transistor  304  has terminals T 17  and T 18  and a control terminal C 7 . The terminal T 17  is electrically connected to the second end e 2  of the storage capacitor Cst and one end of the delivery capacitor Cd which is different from the end of the delivery capacitor Cd electrically connected to the low-level voltage VSS. The terminal T 18  is electrically connected to the first node N 1 . The control terminal C 7  is configured to receive the scan signal SC 5 . In some embodiments, the terminal T 15  of the switching transistor  302  serves as the terminal T 3  of the compensation circuit  300 , the terminal T 16  of the switching transistor  302  and the first end e 1  of the storage capacitor Cst serves as the terminal T 4  of the compensation circuit  300 , the terminal T 18  of the switching transistor  304  serves as the terminal T 5  of the compensation circuit  300 , and the terminal T 17  of the switching transistor  304  serves as the terminal T 6  of the compensation circuit  300 . During the reset segment RS and the compensation segment CS, the switching transistor  302  and the switching transistor  304  are enabled respectively by the scan signal SC 4  and the scan signal SC 5 , such that the reference voltage Vref is applied to modulate the gate voltage of the driving transistor DT during the reset segment RS, and a voltage difference between the first end e 1  and the second end e 2  of the storage capacitor Cst approaches the threshold voltage Vth of the driving transistor DT at the end of the compensating segment CS. During the data input segment DIS, the switching transistor  302  is disabled by the scan signal SC 4 , and the switching transistor  304  is disabled by the scan signal SC 5 , such that the reference voltage Vref is disallowed to be applied to the driving transistor DT, and a voltage difference between two ends of the delivery capacitor Cd is substantially equal to the data voltage Vdata. During the emission segment ES, the switching transistor  302  and the switching transistor  304  are disabled respectively by the scan signal SC 4  and the scan signal SC 5 , such that the threshold voltage Vth of the driving transistor DT and the data voltage Vdata respectively stored in the storage capacitor Cst and the delivery capacitor Cd are applied to modulate the gate voltage of the driving transistor DT. 
     During the recovery segment RCS, one way to recover the threshold voltage shift of the driving transistor DT is as follows. The switching transistor  302  is enabled by the scan signal SC 4  such that the reference voltage Vref with a voltage level lower than the sum of the voltage levels of the low-level voltage VSS, the threshold voltage Vth of the driving transistor DT, and the voltage difference between two ends of the light-emitting device  100  is applied to modulate the gate voltage of the driving transistor DT. Another way to recover the threshold voltage shift of the driving transistor DT is to use the data voltage Vdata instead of the reference voltage Vref. In such a case, the switching transistor  302  and the switching transistor  304  of the compensation circuit  300  are disabled such that the reference voltage Vref is disallowed to be applied to the second node N 2 , and the data voltage Vdata is disallowed to be applied to the first node N 1 . 
     It is noted that from  FIGS. 2A to 2E  the scan signals SC 4  and SC 5  are substantially the same. As a result, in order to save space for a circuit layout, the scan signals SC 4  and SC 5  can be the same scan signal. That is, the terminals C 4  and C 5  of the compensation circuit  300  (or the control terminal C 6  of the switching transistor  302  and the control terminal C 7  of the switching transistor  304 , which are equivalent in the embodiments as illustrated by  FIGS. 3A and 3C ) can be electrically connected to the same scan line in some embodiments. 
     In some embodiments, the data circuit  400  includes a switching transistor  402  (referred to  FIG. 3D ). The switching transistor  402  has terminals T 13  and T 14  and a control terminal C 5 . The terminal T 13  is electrically connected to the data voltage Vdata. The terminal T 14  is electrically connected to the terminal T 6  of the compensation circuit  300  and one end of the delivery capacitor Cd which is different from the end of the delivery capacitor Cd electrically connected to the low-level voltage VSS. The control terminal C 5  is configured to receive the scan signal SC 2 . In some embodiments, the terminal T 13  of the switching transistor  402  serves as the terminal T 7  of the data circuit  400 , the terminal T 14  of the switching transistor  402  serves as the terminal T 8  of the data circuit  400 , and the control terminal C 5  of the switching transistor  402  serves as the control terminal C 2  of the data circuit  400 . During the reset segment RS, the compensation segment CS, and the emission segment ES, the switching transistor  402  is disabled by the scan signal SC 2 . During the data input segment DIS, the switching transistor  402  is enabled by the scan signal SC 2  to control the gate voltage of the driving transistor DT according to the data voltage Vdata. During the recovery segment RCS which uses the reference voltage Vref to recover the threshold voltage shift of the driving transistor DT, the switching transistor  402  is disabled by the scan signal SC 2 . During the recovery segment RCS which uses the data voltage Vdata to recover the threshold voltage shift of the driving transistor DT, the switching transistor  402  is enabled by the scan signal SC 2 , and the data voltage Vdata with a voltage level lower than the voltage level of the sum of the voltage level of the threshold voltage Vth of the driving transistor DT, the low-level voltage VSS, and the voltage difference between two ends of the light-emitting device  100  is applied to recover the threshold voltage shift of the driving transistor DT. 
     Reference is made to  FIG. 5 .  FIG. 5  is a schematic diagram of a light-emitting device driving circuit  1000 - 2  according to some embodiments of the present disclosure. The difference between embodiments as illustrated by  FIG. 5  and the embodiments as illustrated by  FIG. 3A  is that positions of the light-emitting device  100  and the reset circuit  200  in the circuit are exchanged. Therefore, a current provided by the driving transistor DT which is driven by the driving voltage VDD flows through the light-emitting device  100 , the reset circuit  200 , and the low-level voltage line LL in sequence in the embodiments as illustrated by  FIG. 5 . 
     Reference is made to  FIGS. 6A to 6C  and  FIGS. 7A to 7D .  FIG. 6A  is a schematic diagram of a light-emitting device driving circuit  1000 ′ according to some embodiments of the present disclosure.  FIG. 6B  is a schematic diagram of a reset circuit  200 ′ according to some embodiments of the present disclosure.  FIG. 6C  is a timing diagram of an operation for the light-emitting device driving circuit  1000 ′ according to some embodiments of the present disclosure.  FIG. 7A  is the light-emitting device driving circuit  1000 ′ operated during the reset segment RS according to some embodiments of the present disclosure.  FIG. 7B  is the light-emitting device driving circuit  1000 ′ operated during the compensation segment CS according to some embodiments of the present disclosure.  FIG. 7C  is the light-emitting device driving circuit  1000 ′ operated during the data input segment DIS according to some embodiments of the present disclosure.  FIG. 7D  is the light-emitting device driving circuit  1000 ′ operated during the emission segment ES according to some embodiments of the present disclosure. A difference between embodiments as illustrated by  FIG. 6A  and the embodiments as illustrated by  FIG. 3A  is that a reset circuit  200 ′ as shown in the embodiments illustrated by  FIG. 6A  further includes a switching transistor  204  compared to the reset circuit  200  as shown in the embodiments illustrated by  FIG. 3A . The switching transistor  204  has terminals T 11  and T 12  and a control terminal C 3 ′. The terminal T 11  is electrically connected to the first node N 1 . The terminal T 12  is electrically connected to the low-level voltage VSS. The control terminal C 3 ′ is configured to receive a scan signal SC 3 . During the reset segment RS, as illustrated by  FIG. 7A , the switching transistor  204  is enabled by the scan signal SC 3 , such that a voltage level of the first node N 1  is equal to the low-level voltage VSS. The switching transistor  202  can be enabled or disabled during the reset segment RS. During the compensation segment CS, as illustrated by  FIG. 7B , the switching transistor  202  and the switching transistor  204  are disabled respectively by the scan signal SC 1  and the scan signal SC 3 , such that the first node N 1  is not electrically connected to the low-level voltage VSS. During the data input segment DIS, as illustrated by  FIG. 7C , the switching transistor  204  is disabled by the scan signal SC 3 . During the emission segment ES, as illustrated by  FIG. 7D , the switching transistor  202  is enabled by the scan signal SC 1  and the switching transistor  204  is disabled by the scan signal SC 3 . During the recovery segment RCS which uses the reference voltage Vref to recover the threshold voltage shift of the driving transistor DT, the switching transistor  204  is enabled by the scan signal SC 3 , and during the recovery segment RCS which uses the data voltage Vdata to recover the threshold voltage shift of the driving transistor DT, the switching transistor  204  is also disabled by the scan signal SC 3 . It is noteworthy that in the embodiments illustrated by  FIGS. 6A to 6C , a current do not flow through the light-emitting device  100  during the reset segment RS (and also the recovery segment RCS). Therefore, the voltage level of the reference voltage Vref applied during the reset segment RS shall be higher than a sum of the voltage levels of the threshold voltage Vth of the driving transistor DT and the low-level voltage VSS, and a voltage level of the reference voltage Vref applied during the recovery segment RCS shall be lower than the sum of the voltage levels of the threshold voltage Vth of the driving transistor DT and the low-level voltage VSS. Noted that the parameter “the voltage difference between two ends of the light-emitting device  100 ” is absent in the embodiments illustrated by  FIGS. 6A to 6C . 
     Reference is made to  FIG. 8 .  FIG. 8  is a schematic diagram of a light-emitting device driving circuit  2000  according to some embodiments of the present disclosure. Transistors as shown in the embodiments illustrated by  FIGS. 3A, 4A to 4D, 5, 6A, and 7A to 7D  are n-channel transistors, such as a hydrogenated amorphous silicon (a-Si:H) transistor, an indium gallium zinc oxide (IGZO) transistor, or a n-type metal-oxide-semiconductor field effect transistor (NMOSFET). In some embodiments as illustrated by  FIG. 8 , the transistors are p-channel transistors, such as a low-temperature poly-silicon (LTPS) transistor. Similar to the embodiments illustrated by  FIG. 3A  and  FIG. 5 , positions of a light-emitting device and a reset circuit directly connected to the light-emitting device as shown in  FIG. 8  can be exchanged in some other embodiments. The connection relations among electronic elements in the light-emitting device driving circuit  2000  as shown in  FIG. 8  are substantially reversed as compared to the light-emitting device driving circuit  1000 - 1 ,  1000 - 2 , and  1000 ′ and will not be described herein in detail. 
     In summary, a light-emitting device driving circuit is provided to compensate a threshold voltage shift of a driving transistor used to drive a light-emitting device. In addition, a precision of controlling brightness in a low grayscale region of the light-emitting device is enhanced. Furthermore, a resolution of the light-emitting device driving circuit can be greatly enhanced since duration for waiting a compensation segment can be technically avoided within the scope of the light-emitting device driving circuit present in the embodiments of the present disclosure. 
     Although the present disclosure has been described in considerable detail with reference to certain embodiments thereof, other embodiments are possible. Therefore, the spirit and scope of the appended claims should not be limited to the description of the embodiments contained herein. 
     It will be apparent to those skilled in the art that various modifications and variations can be made to the structure of the present disclosure without departing from the scope or spirit of the disclosure. In view of the foregoing, it is intended that the present disclosure cover modifications and variations of this disclosure provided they fall within the scope of the following claims.