Patent Publication Number: US-10764762-B2

Title: Apparatus and methods for distributing a communication signal obtained from ultra-wideband electromagnetic waves

Description:
FIELD OF THE DISCLOSURE 
     The subject disclosure relates to an apparatus and methods distributing a communication signal obtained from ultra-wideband electromagnetic waves. 
     BACKGROUND 
     As smart phones and other portable devices increasingly become ubiquitous, and data usage increases, macrocell base station devices and existing wireless infrastructure in turn require higher bandwidth capability in order to address the increased demand. To provide additional mobile bandwidth, small cell deployment is being pursued, with microcells and picocells providing coverage for much smaller areas than traditional macrocells. 
     In addition, most homes and businesses have grown to rely on broadband data access for services such as voice, video and Internet browsing, etc. Broadband access networks include satellite, 4G or 5G wireless, power line communication, fiber, cable, and telephone networks. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       Reference will now be made to the accompanying drawings, which are not necessarily drawn to scale, and wherein: 
         FIG. 1  is a block diagram illustrating an example, non-limiting embodiment of a guided-wave communications system in accordance with various aspects described herein. 
         FIG. 2  is a block diagram illustrating an example, non-limiting embodiment of a transmission device in accordance with various aspects described herein. 
         FIG. 3  is a graphical diagram illustrating an example, non-limiting embodiment of an electromagnetic field distribution in accordance with various aspects described herein. 
         FIG. 4  is a graphical diagram illustrating an example, non-limiting embodiment of an electromagnetic field distribution in accordance with various aspects described herein. 
         FIG. 5A  is a graphical diagram illustrating an example, non-limiting embodiment of a frequency response in accordance with various aspects described herein. 
         FIG. 5B  is a graphical diagram illustrating example, non-limiting embodiments of a longitudinal cross-section of an insulated wire depicting fields of guided electromagnetic waves at various operating frequencies in accordance with various aspects described herein. 
         FIG. 6  is a graphical diagram illustrating an example, non-limiting embodiment of an electromagnetic field distribution in accordance with various aspects described herein. 
         FIG. 7  is a block diagram illustrating an example, non-limiting embodiment of an arc coupler in accordance with various aspects described herein. 
         FIG. 8  is a block diagram illustrating an example, non-limiting embodiment of an arc coupler in accordance with various aspects described herein. 
         FIG. 9A  is a block diagram illustrating an example, non-limiting embodiment of a stub coupler in accordance with various aspects described herein. 
         FIG. 9B  is a diagram illustrating an example, non-limiting embodiment of an electromagnetic distribution in accordance with various aspects described herein. 
         FIG. 10  is a block diagram illustrating an example, non-limiting embodiment of a coupler and transceiver in accordance with various aspects described herein. 
         FIG. 11  is a block diagram illustrating an example, non-limiting embodiment of a dual stub coupler in accordance with various aspects described herein. 
         FIG. 12  is a block diagram illustrating an example, non-limiting embodiment of a repeater system in accordance with various aspects described herein. 
         FIG. 13  illustrates a block diagram illustrating an example, non-limiting embodiment of a bidirectional repeater in accordance with various aspects described herein. 
         FIG. 14  is a block diagram illustrating an example, non-limiting embodiment of a waveguide system in accordance with various aspects described herein. 
         FIG. 15  is a block diagram illustrating an example, non-limiting embodiment of a guided-wave communications system in accordance with various aspects described herein. 
         FIGS. 16A &amp; 16B  are block diagrams illustrating an example, non-limiting embodiment of a system for managing a power grid communication system in accordance with various aspects described herein. 
         FIG. 17A  illustrates a flow diagram of an example, non-limiting embodiment of a method for detecting and mitigating disturbances occurring in a communication network of the system of  FIGS. 16A and 16B . 
         FIG. 17B  illustrates a flow diagram of an example, non-limiting embodiment of a method for detecting and mitigating disturbances occurring in a communication network of the system of  FIGS. 16A and 16B . 
         FIG. 18A  is a block diagram illustrating an example, non-limiting embodiment of a transmission medium for propagating guided electromagnetic waves. 
         FIG. 18B  is a block diagram illustrating an example, non-limiting embodiment of bundled transmission media in accordance with various aspects described herein. 
         FIG. 18C  is a block diagram illustrating an example, non-limiting embodiment of exposed stubs from the bundled transmission media for use as antennas in accordance with various aspects described herein. 
         FIGS. 18D, 18E, 18F, 18G, 18H, 18I, 18J and 18K  are block diagrams illustrating example, non-limiting embodiments of a waveguide device for transmitting or receiving electromagnetic waves in accordance with various aspects described herein. 
         FIGS. 19A and 19B  are block diagrams illustrating example, non-limiting embodiments of a dielectric antenna and corresponding gain and field intensity plots in accordance with various aspects described herein. 
         FIG. 19C  is a block diagram illustrating an example, non-limiting embodiments of a dielectric antenna coupled to a lens in accordance with various aspects described herein. 
         FIG. 19D  is a block diagram illustrating an example, non-limiting embodiment of near-field and far-field signals emitted by the dielectric antenna of  FIG. 19G  in accordance with various aspects described herein. 
         FIG. 19E  is a block diagram of an example, non-limiting embodiment of a dielectric antenna in accordance with various aspects described herein. 
         FIG. 19F  is a block diagram of an example, non-limiting embodiment of an array of dielectric antennas configurable for steering wireless signals in accordance with various aspects described herein. 
         FIGS. 20A and 20B  are block diagrams illustrating example, non-limiting embodiments of the transmission medium of  FIG. 18A  used for inducing guided electromagnetic waves on power lines supported by utility poles. 
         FIG. 20C  is a block diagram of an example, non-limiting embodiment of a communication network in accordance with various aspects described herein. 
         FIG. 20D  is a block diagram of an example, non-limiting embodiment of an antenna mount for use in a communication network in accordance with various aspects described herein. 
         FIG. 20E  is a block diagram of an example, non-limiting embodiment of an antenna mount for use in a communication network in accordance with various aspects described herein. 
         FIG. 21A  illustrates a flow diagram of an example, non-limiting embodiment of a method for transmitting downlink signals. 
         FIG. 21B  illustrates a flow diagram of an example, non-limiting embodiment of a method for transmitting uplink signals. 
         FIG. 21C  is a block diagram illustrating an example, non-limiting embodiment of electric field characteristics of a hybrid wave versus a Goubau wave in accordance with various aspects described herein. 
         FIG. 21D  is a block diagram illustrating an example, non-limiting embodiment of mode sizes of hybrid waves at various operating frequencies in accordance with various aspects described herein. 
         FIGS. 22A and 22B  are block diagrams illustrating example, non-limiting embodiments of a waveguide device for launching hybrid waves in accordance with various aspects described herein. 
         FIGS. 23A, 23B, and 23C  are block diagrams illustrating example, non-limiting embodiments of a waveguide device in accordance with various aspects described herein. 
         FIG. 24  is a block diagram illustrating an example, non-limiting embodiment of a waveguide device in accordance with various aspects described herein. 
         FIG. 25A  is a block diagram illustrating an example, non-limiting embodiment of a waveguide device in accordance with various aspects described herein. 
         FIGS. 25B, 25C, and 25D  are block diagrams illustrating example, non-limiting embodiments of wave modes and electric field plots in accordance with various aspects described herein. 
         FIG. 26  illustrates a flow diagram of an example, non-limiting embodiment of a method for managing electromagnetic waves. 
         FIG. 27  is a block diagram illustrating an example, non-limiting embodiment of substantially orthogonal wave modes in accordance with various aspects described herein. 
         FIG. 28  is a block diagram illustrating an example, non-limiting embodiment of an insulated conductor in accordance with various aspects described herein. 
         FIG. 29  is a block diagram illustrating an example, non-limiting embodiment of an uninsulated conductor in accordance with various aspects described herein. 
         FIG. 30  is a block diagram illustrating an example, non-limiting embodiment of an oxide layer formed on the uninsulated conductor of  FIG. 25A  in accordance with various aspects described herein. 
         FIG. 31  is a block diagram illustrating example, non-limiting embodiments of spectral plots in accordance with various aspects described herein. 
         FIG. 32  is a block diagram illustrating example, non-limiting embodiments of spectral plots in accordance with various aspects described herein. 
         FIG. 33  is a block diagram illustrating example, non-limiting embodiments for transmitting orthogonal wave modes in accordance with various aspects described herein. 
         FIG. 34  is a block diagram illustrating example, non-limiting embodiments for transmitting orthogonal wave modes in accordance with various aspects described herein. 
         FIG. 35  is a block diagram illustrating example, non-limiting embodiments for selectively receiving a wave mode in accordance with various aspects described herein. 
         FIG. 36  is a block diagram illustrating example, non-limiting embodiments for selectively receiving a wave mode in accordance with various aspects described herein. 
         FIG. 37  is a block diagram illustrating example, non-limiting embodiments for selectively receiving a wave mode in accordance with various aspects described herein. 
         FIG. 38  is a block diagram illustrating example, non-limiting embodiments for selectively receiving a wave mode in accordance with various aspects described herein. 
         FIG. 39  is a block diagram illustrating example, non-limiting embodiments of a polyrod antenna for transmitting wireless signals in accordance with various aspects described herein. 
         FIG. 40  is a block diagram illustrating an example, non-limiting embodiment of electric field characteristics of transmitted signals from a polyrod antenna in accordance with various aspects described herein. 
         FIGS. 41 and 42  are block diagrams illustrating an example, non-limiting embodiment of a polyrod antenna array in accordance with various aspects described herein. 
         FIGS. 43A, and 43B  are block diagrams illustrating an example, non-limiting embodiment of an antenna, and electric field characteristics of transmitted signals from the antenna in accordance with various aspects described herein. 
         FIG. 44A  is a block diagram illustrating an example, non-limiting embodiment of a communication system in accordance with various aspects described herein. 
         FIG. 44B  is a block diagram illustrating an example, non-limiting embodiment of a portion of the communication system of  FIG. 44A  in accordance with various aspects described herein. 
         FIG. 44C  is a graphical diagram illustrating an example, non-limiting embodiment of downlink and uplink communication techniques for enabling a base station to communicate with communication nodes in accordance with various aspects described herein. 
         FIG. 44D  is a graphical diagram illustrating an example, non-limiting embodiment of a frequency spectrum in accordance with various aspects described herein. 
         FIG. 44E  is a graphical diagram illustrating an example, non-limiting embodiment of a frequency spectrum in accordance with various aspects described herein. 
         FIG. 45  is a block diagram illustrating an example, non-limiting embodiment of a communication system that utilizes beam steering in accordance with various aspects described herein. 
         FIGS. 46A, 46B, 46C, 46D, 46E, and 46F  are graphical diagrams illustrating example, non-limiting embodiments of network configurations of waveguide systems in accordance with various aspects described herein. 
         FIG. 46G  is a graphical diagram illustrating an example, non-limiting embodiment of a device for transmitting ultra-wideband electromagnetic pulses based on a communication signal in accordance with various aspects described herein. 
         FIGS. 46H and 46I  is a graphical diagram illustrating an example, non-limiting embodiment of timing diagrams for exchanging ultra-wideband electromagnetic pulses between communication nodes in accordance with various aspects described herein. 
         FIG. 46J  is a graphical diagram illustrating an example, non-limiting embodiment of a device for receiving ultra-wideband electromagnetic pulses and generating therefrom a communication signal in accordance with various aspects described herein. 
         FIG. 46K  illustrates a flow diagram of an example, non-limiting embodiment of a method for transmitting ultra-wideband electromagnetic pulses based on a communication signal in accordance with various aspects described herein. 
         FIG. 46L  illustrates a flow diagram of an example, non-limiting embodiment of a method for receiving ultra-wideband electromagnetic pulses and generating therefrom a communication signal in accordance with various aspects described herein. 
         FIG. 46M  illustrates a flow diagram of an example, non-limiting embodiment of a method for transmitting ultra-wideband surface waves based on a communication signal in accordance with various aspects described herein. 
         FIG. 46N  illustrates a flow diagram of an example, non-limiting embodiment of a method for receiving ultra-wideband surface and generating therefrom a communication signal in accordance with various aspects described herein. 
         FIG. 47  is a block diagram of an example, non-limiting embodiment of a computing environment in accordance with various aspects described herein. 
         FIG. 48  is a block diagram of an example, non-limiting embodiment of a mobile network platform in accordance with various aspects described herein. 
         FIG. 49  is a block diagram of an example, non-limiting embodiment of a communication device in accordance with various aspects described herein. 
     
    
    
     DETAILED DESCRIPTION 
     One or more embodiments are now described with reference to the drawings, wherein like reference numerals are used to refer to like elements throughout the drawings. In the following description, for purposes of explanation, numerous details are set forth in order to provide a thorough understanding of the various embodiments. It is evident, however, that the various embodiments can be practiced without these details (and without applying to any particular networked environment or standard). 
     In an embodiment, a guided wave communication system is presented for sending and receiving communication signals such as data or other signaling via guided electromagnetic waves. The guided electromagnetic waves include, for example, surface waves or other electromagnetic waves that are bound to or guided by a transmission medium as described herein. It will be appreciated that a variety of transmission media can be utilized with guided wave communications without departing from example embodiments. Examples of such transmission media can include one or more of the following, either alone or in one or more combinations: wires, whether insulated or not, and whether single-stranded or multi-stranded; conductors of other shapes or configurations including unshielded twisted pair cables including single twisted pairs, Category 5e and other twisted pair cable bundles, other wire bundles, cables, rods, rails, pipes; non-conductors such as dielectric pipes, rods, rails, or other dielectric members; combinations of conductors and dielectric materials; or other guided wave transmission media. 
     The inducement of guided electromagnetic waves that propagate along a transmission medium can be independent of any electrical potential, charge or current that is injected or otherwise transmitted through the transmission medium as part of an electrical circuit. For example, in the case where the transmission medium is a wire, it is to be appreciated that while a small current in the wire may be formed in response to the propagation of the electromagnetic waves guided along the wire, this can be due to the propagation of the electromagnetic wave along the wire surface, and is not formed in response to electrical potential, charge or current that is injected into the wire as part of an electrical circuit. The electromagnetic waves traveling along the wire therefore do not require an electrical circuit (i.e., ground or another electrical return path) to propagate along the wire surface. The wire therefore is a single wire transmission line that is not part of an electrical circuit. For example, electromagnetic waves can propagate along a wire configured as an electrical open circuit. Also, in some embodiments, a wire is not necessary, and the electromagnetic waves can propagate along a single line transmission medium that is not a wire including a single line transmission medium that is conductorless. 
     More generally, “guided electromagnetic waves” or “guided waves” as described by the subject disclosure are affected by the presence of a physical object that is at least a part of the transmission medium (e.g., a bare wire or other conductor, a dielectric including a dielectric core without a conductive shield and/or without an inner conductor, an insulated wire, a conduit or other hollow element whether conductive or not, a bundle of insulated wires that is coated, covered or surrounded by a dielectric or insulator or other wire bundle, or another form of solid, liquid or otherwise non-gaseous transmission medium) so as to be at least partially bound to or guided by the physical object and so as to propagate along a transmission path of the physical object. Such a physical object can operate as at least a part of a transmission medium that guides, by way of one or more interfaces of the transmission medium (e.g., an outer surface, inner surface, an interior portion between the outer and the inner surfaces or other boundary between elements of the transmission medium). In this fashion, a transmission medium may support multiple transmission paths over different surfaces of the transmission medium. For example, a stranded cable or wire bundle may support electromagnetic waves that are guided by the outer surface of the stranded cable or wire bundle, as well as electromagnetic waves that are guided by inner cable surfaces between two, three or more individual strands or wires within the stranded cable or wire bundle. For example, electromagnetic waves can be guided within interstitial areas of a stranded cable, insulated twisted pair wires, or a wire bundle. The guided electromagnetic waves of the subject disclosure are launched from a sending (transmitting) device and propagate along the transmission medium for reception by at least one receiving device. The propagation of guided electromagnetic waves, can carry energy, data and/or other signals along the transmission path from the sending device to the receiving device. 
     As used herein the term “conductor” (based on a definition of the term “conductor” from  IEEE  100 , the Authoritative Dictionary of IEEE Standards Terms,  7 th  Edition, 2000) means a substance or body that allows a current of electricity to pass continuously along it. The terms “insulator”, “conductorless” or “nonconductor” (based on a definition of the term “insulator” from  IEEE  100 , the Authoritative Dictionary of IEEE Standards Terms,  7 th  Edition, 2000) means a device or material in which electrons or ions cannot be moved easily. It is possible for an insulator, or a conductorless or nonconductive material to be intermixed intentionally (e.g., doped) or unintentionally into a resulting substance with a small amount of another material having the properties of a conductor. However, the resulting substance may remain substantially resistant to a flow of a continuous electrical current along the resulting substance. Furthermore, a conductorless member such as a dielectric rod or other conductorless core lacks an inner conductor and a conductive shield. As used herein, the term “eddy current” (based on a definition of the term “conductor” from  IEEE  100 , the Authoritative Dictionary of IEEE Standards Terms,  7 th  Edition, 2000) means a current that circulates in a metallic material as a result of electromotive forces induced by a variation of magnetic flux. Although it may be possible for an insulator, conductorless or nonconductive material in the foregoing embodiments to allow eddy currents that circulate within the doped or intermixed conductor and/or a very small continuous flow of an electrical current along the extent of the insulator, conductorless or nonconductive material, any such continuous flow of electrical current along such an insulator, conductorless or nonconductive material is de minimis compared to the flow of an electrical current along a conductor. Accordingly, in the subject disclosure an insulator, and a conductorless or nonconductor material are not considered to be a conductor. The term “dielectric” means an insulator that can be polarized by an applied electric field. When a dielectric is placed in an electric field, electric charges do not continuously flow through the material as they do in a conductor, but only slightly shift from their average equilibrium positions causing dielectric polarization. The terms “conductorless transmission medium or non-conductor transmission medium” can mean a transmission medium consisting of any material (or combination of materials) that may or may not contain one or more conductive elements but lacks a continuous conductor between the sending and receiving devices along the conductorless transmission medium or non-conductor transmission medium—similar or identical to the aforementioned properties of an insulator, conductorless or nonconductive material. 
     Unlike free space propagation of wireless signals such as unguided (or unbounded) electromagnetic waves that decrease in intensity inversely by the square of the distance traveled by the unguided electromagnetic waves, guided electromagnetic waves can propagate along a transmission medium with less loss in magnitude per unit distance than experienced by unguided electromagnetic waves. 
     Unlike electrical signals, guided electromagnetic waves can propagate from a sending device to a receiving device without requiring a separate electrical return path between the sending device and the receiving device. As a consequence, guided electromagnetic waves can propagate from a sending device to a receiving device along a conductorless transmission medium including a transmission medium having no conductive components (e.g., a dielectric strip, rod, or pipe), or via a transmission medium having no more than a single conductor (e.g., a single bare wire or insulated wire configured in an open electrical circuit). Even if a transmission medium includes one or more conductive components and the guided electromagnetic waves propagating along the transmission medium generate currents that flow in the one or more conductive components in a direction of the guided electromagnetic waves, such guided electromagnetic waves can propagate along the transmission medium from a sending device to a receiving device without requiring a flow of opposing currents on an electrical return path between the sending device and the receiving device (i.e., in an electrical open circuit configuration). 
     In a non-limiting illustration, consider electrical systems that transmit and receive electrical signals between sending and receiving devices by way of conductive media. Such systems generally rely on an electrical forward path and an electrical return path. For instance, consider a coaxial cable having a center conductor and a ground shield that are separated by an insulator. Typically, in an electrical system a first terminal of a sending (or receiving) device can be connected to the center conductor, and a second terminal of the sending (or receiving) device can be connected to the ground shield or other second conductor. If the sending device injects an electrical signal in the center conductor via the first terminal, the electrical signal will propagate along the center conductor causing forward currents in the center conductor, and return currents in the ground shield or other second conductor. The same conditions apply for a two terminal receiving device. 
     In contrast, consider a guided wave communication system such as described in the subject disclosure, which can utilize different embodiments of a transmission medium (including among others a coaxial cable) for transmitting and receiving guided electromagnetic waves without requiring an electrical return path. In one embodiment, for example, the guided wave communication system of the subject disclosure can be configured to induce guided electromagnetic waves that propagate along an outer surface of a coaxial cable. Although the guided electromagnetic waves can cause forward currents on the ground shield, the guided electromagnetic waves do not require return currents on, for example, the center conductor to enable the guided electromagnetic waves to propagate along the outer surface of the coaxial cable. The same can be said of other transmission media used by a guided wave communication system for the transmission and reception of guided electromagnetic waves. For example, guided electromagnetic waves induced by the guided wave communication system on a bare wire, an insulated wire, or a dielectric transmission medium (e.g., a dielectric core with no conductive materials), can propagate along the bare wire, the insulated bare wire, or the dielectric transmission medium without requiring return currents on an electrical return path. 
     Consequently, electrical systems that require forward and return conductors for carrying corresponding forward and reverse currents on conductors to enable the propagation of electrical signals injected by a sending device are distinct from guided wave systems that induce guided electromagnetic waves on an interface of a transmission medium without requiring an electrical return path to enable the propagation of the guided electromagnetic waves along the interface of the transmission medium. 
     It is further noted that guided electromagnetic waves as described in the subject disclosure can have an electromagnetic field structure that lies primarily or substantially on an outer surface of a transmission medium so as to be bound to or guided by the outer surface of the transmission medium and so as to propagate non-trivial distances on or along the outer surface of the transmission medium. In other embodiments, guided electromagnetic waves can have an electromagnetic field structure that lies primarily or substantially below an outer surface of a transmission medium so as to be bound to or guided by an inner material of the transmission medium (e.g., dielectric material) and so as to propagate non-trivial distances within the inner material of the transmission medium. In other embodiments, guided electromagnetic waves can have an electromagnetic field structure that lies within a region that is partially below and partially above an outer surface of a transmission medium so as to be bound to or guided by this region of the transmission medium and so as to propagate non-trivial distances along this region of the transmission medium. The desired electromagnetic field structure in an embodiment may vary based upon a variety of factors, including the desired transmission distance, the characteristics of the transmission medium itself, and environmental conditions/characteristics outside of the transmission medium (e.g., presence of rain, fog, atmospheric conditions, etc.). 
     Various embodiments described herein relate to coupling devices, that can be referred to as “waveguide coupling devices”, “waveguide couplers” or more simply as “couplers”, “coupling devices” or “launchers” for launching and/or receiving/extracting guided electromagnetic waves to and from a transmission medium, wherein a wavelength of the guided electromagnetic waves can be small compared to one or more dimensions of the coupling device and/or the transmission medium such as the circumference of a wire or other cross sectional dimension. Such electromagnetic waves can operate at millimeter wave frequencies (e.g., 30 to 300 GHz), or lower than microwave frequencies such as 300 MHz to 30 GHz. Electromagnetic waves can be induced to propagate along a transmission medium by a coupling device, such as: a strip, arc or other length of dielectric material; a millimeter wave integrated circuit (MMIC), a horn, monopole, rod, slot or other antenna; an array of antennas; a magnetic resonant cavity or other resonant coupler; a coil, a strip line, a coaxial waveguide or other waveguide and/or other coupling device. In operation, the coupling device receives an electromagnetic wave from a transmitter or transmission medium. The electromagnetic field structure of the electromagnetic wave can be carried below an outer surface of the coupling device, substantially on the outer surface of the coupling device, or a combination thereof. When the coupling device is in close proximity to a transmission medium, at least a portion of an electromagnetic wave couples to or is bound to the transmission medium, and continues to propagate as guided electromagnetic waves along the transmission medium. In a reciprocal fashion, a coupling device can receive or extract at least a portion of the guided electromagnetic waves from a transmission medium and transfer these electromagnetic waves to a receiver. The guided electromagnetic waves launched and/or received by the coupling device propagate along the transmission medium from a sending device to a receiving device without requiring an electrical return path between the sending device and the receiving device. In this circumstance, the transmission medium acts as a waveguide to support the propagation of the guided electromagnetic waves from the sending device to the receiving device. 
     According to an example embodiment, a surface wave is a type of guided wave that is guided by a surface of a transmission medium, such as an exterior or outer surface or an interior or inner surface including an interstitial surface of the transmission medium such as the interstitial area between wires in a multistranded cable, insulated twisted pair wires, or wire bundle, and/or another surface of the transmission medium that is adjacent to or exposed to another type of medium having different properties (e.g., dielectric properties). Indeed, in an example embodiment, a surface of the transmission medium that guides a surface wave can represent a transitional surface between two different types of media. For example, in the case of a bare wire or uninsulated wire, the surface of the wire can be the outer or exterior conductive surface of the bare wire or uninsulated wire that is exposed to air or free space. As another example, in the case of insulated wire, the surface of the wire can be the conductive portion of the wire that meets an inner surface of the insulator portion of the wire. A surface of the transmission medium can be any one of an inner surface of an insulator surface of a wire or a conductive surface of the wire that is separated by a gap composed of, for example, air or free space. A surface of a transmission medium can otherwise be any material region of the transmission medium. For example, the surface of the transmission medium can be an inner portion of an insulator disposed on a conductive portion of the wire that meets the insulator portion of the wire. The surface that guides an electromagnetic wave can depend upon the relative differences in the properties (e.g., dielectric properties) of the insulator, air, and/or the conductor and further dependent on the frequency and propagation mode or modes of the guided wave. 
     According to an example embodiment, the term “about” a wire or other transmission medium used in conjunction with a guided wave can include fundamental guided wave propagation modes such as a guided waves having a circular or substantially circular field pattern/distribution, a symmetrical electromagnetic field pattern/distribution (e.g., electric field or magnetic field) or other fundamental mode pattern at least partially around a wire or other transmission medium. Unlike Zenneck waves that propagate along a single planar surface of a planar transmission medium, the guided electromagnetic waves of the subject disclosure that are bound to a transmission medium can have a non-planar surface have electromagnetic field patterns that surround or circumscribe, at least in part, the non-planar surface of the transmission medium with electromagnetic energy in all directions, or in all but a finite number of azimuthal null directions characterized by field strengths that approach zero field strength for infinitesimally small azimuthal widths. 
     For example, such non-circular field distributions can be unilateral or multi-lateral with one or more axial lobes characterized by relatively higher field strength and/or one or more nulls directions of zero field strength or substantially zero-field strength or null regions characterized by relatively low-field strength, zero-field strength and/or substantially zero-field strength. Further, the field distribution can otherwise vary as a function of azimuthal orientation around a transmission medium such that one or more angular regions around the transmission medium have an electric or magnetic field strength (or combination thereof) that is higher than one or more other angular regions of azimuthal orientation, according to an example embodiment. It will be appreciated that the relative orientations or positions of the guided wave higher order modes, particularly asymmetrical modes, can vary as the guided wave travels along the wire. 
     In addition, when a guided wave propagates “about” a wire or other type of transmission medium, it can do so according to a guided wave propagation mode that includes not only the fundamental wave propagation modes (e.g., zero order modes), but additionally or alternatively, non-fundamental wave propagation modes such as higher-order guided wave modes (e.g., 1 st  order modes, 2 nd  order modes, etc.). Higher-order modes include symmetrical modes that have a circular or substantially circular electric or magnetic field distribution and/or a symmetrical electric or magnetic field distribution, or asymmetrical modes and/or other guided (e.g., surface) waves that have non-circular and/or asymmetrical field distributions around the wire or other transmission medium. For example, the guided electromagnetic waves of the subject disclosure can propagate along a transmission medium from the sending device to the receiving device or along a coupling device via one or more guided wave modes such as a fundamental transverse magnetic (TM) TM00 mode (or Goubau mode), a fundamental hybrid mode (EH or HE) “EH00” mode or “HE00” mode, a transverse electromagnetic “TEMnm” mode, a total internal reflection (TIR) mode or any other mode such as EHnm, HEnm or TMnm, where n and/or m have integer values greater than or equal to 0, and other fundamental, hybrid and non-fundamental wave modes. 
     As used herein, the term “guided wave mode” refers to a guided wave propagation mode of a transmission medium, coupling device or other system component of a guided wave communication system that propagates for non-trivial distances along the length of the transmission medium, coupling device or other system component. 
     As used herein, the term “millimeter-wave” can refer to electromagnetic waves/signals that fall within the “millimeter-wave frequency band” of 30 GHz to 300 GHz. The term “microwave” can refer to electromagnetic waves/signals that fall within a “microwave frequency band” of 300 MHz to 300 GHz. The term “radio frequency” or “RF” can refer to electromagnetic waves/signals that fall within the “radio frequency band” of 10 kHz to 1 THz. It is appreciated that wireless signals, electrical signals, and guided electromagnetic waves as described in the subject disclosure can be configured to operate at any desirable frequency range, such as, for example, at frequencies within, above or below millimeter-wave and/or microwave frequency bands. In particular, when a coupling device or transmission medium includes a conductive element, the frequency of the guided electromagnetic waves that are carried by the coupling device and/or propagate along the transmission medium can be below the mean collision frequency of the electrons in the conductive element. Further, the frequency of the guided electromagnetic waves that are carried by the coupling device and/or propagate along the transmission medium can be a non-optical frequency, e.g., a radio frequency below the range of optical frequencies that begins at 1 THz. 
     It is further appreciated that a transmission medium as described in the subject disclosure can be configured to be opaque or otherwise resistant to (or at least substantially reduce) a propagation of electromagnetic waves operating at optical frequencies (e.g., greater than 1 THz). 
     As used herein, the term “antenna” can refer to a device that is part of a transmitting or receiving system to transmit/radiate or receive free space wireless signals. 
     In accordance with one or more embodiments, a method of the subject disclosure can include receiving, by an access point, a first communication signal from a waveguide system, wherein the waveguide system receives a first plurality of ultra-wideband electromagnetic wave pulses that propagates along a surface of a transmission medium without requiring an electrical return path, and wherein the waveguide system obtains the first communication signal from the first plurality of ultra-wideband electromagnetic wave pulses, and transmitting, by the access point, a first wireless signal to a communication device, wherein the first wireless signal conveys the first communication signal received from the waveguide system. 
     In accordance with one or more embodiments, an access point of the subject disclosure can include a processing system including a processor, and a memory that stores executable instructions that, when executed by the processing system, facilitate performance of operations. The operations can include receiving from a system a modulated signal in a first spectral segment, wherein the system is configured to receive a plurality of ultra-wideband electromagnetic wave pulses via a transmission medium and extract a communication signal from the plurality of ultra-wideband electromagnetic wave pulses, wherein the plurality of ultra-wideband electromagnetic wave pulses conveys the modulated signal in the first spectral segment without modifying a signaling protocol of the modulated signal, and wherein the plurality of ultra-wideband electromagnetic wave pulses operates in a second spectral segment that differs from the first spectral segment, and transmitting the modulated signal in the first spectral segment to a communication device. 
     In accordance with one or more embodiments, an access point of the subject disclosure can include a processing system including a processor, and a memory that stores executable instructions that, when executed by the processing system, facilitate performance of operations. The operations can include receiving from a system a modulated signal in a first spectral segment, wherein the system is configured to receive a plurality of ultra-wideband electromagnetic wave pulses via a transmission medium and extract the modulated signal in the first spectral segment from a plurality of modulated signals conveyed by the plurality of ultra-wideband electromagnetic wave pulses, and wherein the plurality of ultra-wideband electromagnetic wave pulses operates in a second spectral segment that differs from the first spectral segment, and transmitting the modulated signal in the first spectral segment to a communication device. 
     Referring now to  FIG. 1 , a block diagram  100  illustrating an example, non-limiting embodiment of a guided wave communications system is shown. In operation, a transmission device  101  receives one or more communication signals  110  from a communication network or other communications device that includes data and generates guided waves  120  to convey the data via the transmission medium  125  to the transmission device  102 . The transmission device  102  receives the guided waves  120  and converts them to communication signals  112  that include the data for transmission to a communications network or other communications device. The guided waves  120  can be modulated to convey data via a modulation technique such as phase shift keying, frequency shift keying, quadrature amplitude modulation, amplitude modulation, multi-carrier modulation such as orthogonal frequency division multiplexing and via multiple access techniques such as frequency division multiplexing, time division multiplexing, code division multiplexing, multiplexing via differing wave propagation modes and via other modulation and access strategies. 
     The communication network or networks can include a wireless communication network such as a mobile data network, a cellular voice and data network, a wireless local area network (e.g., WiFi or an IEEE 802.xx network), a satellite communications network, a personal area network or other wireless network. The communication network or networks can also include a wired communication network such as a telephone network, an Ethernet network, a local area network, a wide area network such as the Internet, a broadband access network, a cable network, a fiber optic network, or other wired network. The communication devices can include a network edge device, bridge device or home gateway, a set-top box, broadband modem, telephone adapter, access point, base station, or other fixed communication device, a mobile communication device such as an automotive gateway or automobile, laptop computer, tablet, smartphone, cellular telephone, or other communication device. 
     In an example embodiment, the guided wave communication system  100  can operate in a bi-directional fashion where transmission device  102  receives one or more communication signals  112  from a communication network or device that includes other data and generates guided waves  122  to convey the other data via the transmission medium  125  to the transmission device  101 . In this mode of operation, the transmission device  101  receives the guided waves  122  and converts them to communication signals  110  that include the other data for transmission to a communications network or device. The guided waves  122  can be modulated to convey data via a modulation technique such as phase shift keying, frequency shift keying, quadrature amplitude modulation, amplitude modulation, multi-carrier modulation such as orthogonal frequency division multiplexing and via multiple access techniques such as frequency division multiplexing, time division multiplexing, code division multiplexing, multiplexing via differing wave propagation modes and via other modulation and access strategies. 
     The transmission medium  125  can include a cable having at least one inner portion surrounded by a dielectric material such as an insulator or other dielectric cover, coating or other dielectric material, the dielectric material having an outer surface and a corresponding circumference. In an example embodiment, the transmission medium  125  operates as a single-wire transmission line to guide the transmission of an electromagnetic wave. When the transmission medium  125  is implemented as a single wire transmission system, it can include a wire. The wire can be insulated or uninsulated, and single-stranded or multi-stranded (e.g., braided). In other embodiments, the transmission medium  125  can contain conductors of other shapes or configurations including wire bundles, cables, rods, rails, pipes. In addition, the transmission medium  125  can include non-conductors such as dielectric pipes, rods, rails, or other dielectric members; combinations of conductors and dielectric materials, conductors without dielectric materials or other guided wave transmission media and/or consist essentially of non-conductors such as dielectric pipes, rods, rails, or other dielectric members that operate without a continuous conductor such as an inner conductor or a conductive shield. It should be noted that the transmission medium  125  can otherwise include any of the transmission media previously discussed. 
     Further, as previously discussed, the guided waves  120  and  122  can be contrasted with radio transmissions over free space/air or conventional propagation of electrical power or signals through the conductor of a wire via an electrical circuit. In addition to the propagation of guided waves  120  and  122 , the transmission medium  125  may optionally contain one or more wires that propagate electrical power or other communication signals in a conventional manner as a part of one or more electrical circuits. 
     Referring now to  FIG. 2 , a block diagram  200  illustrating an example, non-limiting embodiment of a transmission device is shown. The transmission device  101  or  102  includes a communications interface (I/F)  205 , a transceiver  210  and a coupler  220 . 
     In an example of operation, the communications interface  205  receives a communication signal  110  or  112  that includes data. In various embodiments, the communications interface  205  can include a wireless interface for receiving a wireless communication signal in accordance with a wireless standard protocol such as LTE or other cellular voice and data protocol, WiFi or an 802.11 protocol, WIMAX protocol, Ultra Wideband protocol, Bluetooth® protocol, Zigbee® protocol, a direct broadcast satellite (DBS) or other satellite communication protocol or other wireless protocol. In addition or in the alternative, the communications interface  205  includes a wired interface that operates in accordance with an Ethernet protocol, universal serial bus (USB) protocol, a data over cable service interface specification (DOCSIS) protocol, a digital subscriber line (DSL) protocol, a Firewire (IEEE 1394) protocol, or other wired protocol. In additional to standards-based protocols, the communications interface  205  can operate in conjunction with other wired or wireless protocol. In addition, the communications interface  205  can optionally operate in conjunction with a protocol stack that includes multiple protocol layers including a MAC protocol, transport protocol, application protocol, etc. 
     In an example of operation, the transceiver  210  generates an electromagnetic wave based on the communication signal  110  or  112  to convey the data. The electromagnetic wave has at least one carrier frequency and at least one corresponding wavelength. The carrier frequency can be within a millimeter-wave frequency band of 30 GHz-300 GHz, such as 60 GHz or a carrier frequency in the range of 30-40 GHz or a lower frequency band of 300 MHz-30 GHz in the microwave frequency range such as 26-30 GHz, 11 GHz, or 3-6 GHz, but it will be appreciated that other carrier frequencies are possible in other embodiments. In one mode of operation, the transceiver  210  merely upconverts the communications signal or signals  110  or  112  for transmission of the electromagnetic signal in the microwave or millimeter-wave band as a guided electromagnetic wave that is guided by or bound to the transmission medium  125 . In another mode of operation, the communications interface  205  either converts the communication signal  110  or  112  to a baseband or near baseband signal or extracts the data from the communication signal  110  or  112  and the transceiver  210  modulates a high-frequency carrier with the data, the baseband or near baseband signal for transmission. It should be appreciated that the transceiver  210  can modulate the data received via the communication signal  110  or  112  to preserve one or more data communication protocols of the communication signal  110  or  112  either by encapsulation in the payload of a different protocol or by simple frequency shifting. In the alternative, the transceiver  210  can otherwise translate the data received via the communication signal  110  or  112  to a protocol that is different from the data communication protocol or protocols of the communication signal  110  or  112 . 
     In an example of operation, the coupler  220  couples the electromagnetic wave to the transmission medium  125  as a guided electromagnetic wave to convey the communications signal or signals  110  or  112 . While the prior description has focused on the operation of the transceiver  210  as a transmitter, the transceiver  210  can also operate to receive electromagnetic waves that convey other data from the single wire transmission medium via the coupler  220  and to generate communications signals  110  or  112 , via communications interface  205  that includes the other data. Consider embodiments where an additional guided electromagnetic wave conveys other data that also propagates along the transmission medium  125 . The coupler  220  can also couple this additional electromagnetic wave from the transmission medium  125  to the transceiver  210  for reception. 
     The transmission device  101  or  102  includes an optional training controller  230 . In an example embodiment, the training controller  230  is implemented by a standalone processor or a processor that is shared with one or more other components of the transmission device  101  or  102 . The training controller  230  selects the carrier frequencies, modulation schemes and/or guided wave modes for the guided electromagnetic waves based on testing of the transmission medium  125 , environmental conditions and/or feedback data received by the transceiver  210  from at least one remote transmission device coupled to receive the guided electromagnetic wave. 
     In an example embodiment, a guided electromagnetic wave transmitted by a remote transmission device  101  or  102  conveys data that also propagates along the transmission medium  125 . The data from the remote transmission device  101  or  102  can be generated to include the feedback data. In operation, the coupler  220  also couples the guided electromagnetic wave from the transmission medium  125  and the transceiver receives the electromagnetic wave and processes the electromagnetic wave to extract the feedback data. 
     In an example embodiment, the training controller  230  operates based on the feedback data to evaluate a plurality of candidate frequencies, modulation schemes and/or transmission modes to select a carrier frequency, modulation scheme and/or transmission mode to enhance performance, such as throughput, signal strength, reduce propagation loss, etc. 
     Consider the following example: a transmission device  101  begins operation under control of the training controller  230  by sending a plurality of guided waves as test signals such as pilot waves or other test signals at a corresponding plurality of candidate frequencies and/or candidate modes directed to a remote transmission device  102  coupled to the transmission medium  125 . The guided waves can include, in addition or in the alternative, test data. The test data can indicate the particular candidate frequency and/or guide-wave mode of the signal. In an embodiment, the training controller  230  at the remote transmission device  102  receives the test signals and/or test data from any of the guided waves that were properly received and determines the best candidate frequency and/or guided wave mode, a set of acceptable candidate frequencies and/or guided wave modes, or a rank ordering of candidate frequencies and/or guided wave modes. This selection of candidate frequenc(ies) or/and guided-mode(s) are generated by the training controller  230  based on one or more optimizing criteria such as received signal strength, bit error rate, packet error rate, signal to noise ratio, propagation loss, etc. The training controller  230  generates feedback data that indicates the selection of candidate frequenc(ies) or/and guided wave mode(s) and sends the feedback data to the transceiver  210  for transmission to the transmission device  101 . The transmission device  101  and  102  can then communicate data with one another based on the selection of candidate frequenc(ies) or/and guided wave mode(s). 
     In other embodiments, the guided electromagnetic waves that contain the test signals and/or test data are reflected back, repeated back or otherwise looped back by the remote transmission device  102  to the transmission device  101  for reception and analysis by the training controller  230  of the transmission device  101  that initiated these waves. For example, the transmission device  101  can send a signal to the remote transmission device  102  to initiate a test mode where a physical reflector is switched on the line, a termination impedance is changed to cause reflections, a loop back mode is switched on to couple electromagnetic waves back to the source transmission device  102 , and/or a repeater mode is enabled to amplify and retransmit the electromagnetic waves back to the source transmission device  102 . The training controller  230  at the source transmission device  102  receives the test signals and/or test data from any of the guided waves that were properly received and determines selection of candidate frequenc(ies) or/and guided wave mode(s). 
     While the procedure above has been described in a start-up or initialization mode of operation, each transmission device  101  or  102  can send test signals, evaluate candidate frequencies or guided wave modes via non-test conditions such as normal transmissions or otherwise evaluate candidate frequencies or guided wave modes at other times or continuously as well. In an example embodiment, the communication protocol between the transmission devices  101  and  102  can include an on-request or periodic test mode where either full testing or more limited testing of a subset of candidate frequencies and guided wave modes are tested and evaluated. In other modes of operation, the re-entry into such a test mode can be triggered by a degradation of performance due to a disturbance, weather conditions, etc. In an example embodiment, the receiver bandwidth of the transceiver  210  is either sufficiently wide or swept to receive all candidate frequencies or can be selectively adjusted by the training controller  230  to a training mode where the receiver bandwidth of the transceiver  210  is sufficiently wide or swept to receive all candidate frequencies. 
     Referring now to  FIG. 3 , a graphical diagram  300  illustrating an example, non-limiting embodiment of an electromagnetic field distribution is shown. In this embodiment, a transmission medium  125  in air includes an inner conductor  301  and an insulating jacket  302  of dielectric material, as shown in cross section. The diagram  300  includes different gray-scales that represent differing electromagnetic field strengths generated by the propagation of the guided wave having a non-circular and non-fundamental guided wave mode. 
     In particular, the electromagnetic field distribution corresponds to a modal “sweet spot” that enhances guided electromagnetic wave propagation along an insulated transmission medium and reduces end-to-end transmission loss. In this particular mode, electromagnetic waves are guided by the transmission medium  125  to propagate along an outer surface of the transmission medium—in this case, the outer surface of the insulating jacket  302 . Electromagnetic waves are partially embedded in the insulator and partially radiating on the outer surface of the insulator. In this fashion, electromagnetic waves are “lightly” coupled to the insulator so as to enable electromagnetic wave propagation at long distances with low propagation loss. 
     As shown, the guided wave has a field structure that lies primarily or substantially outside of the transmission medium  125  that serves to guide the electromagnetic waves. The regions inside the conductor  301  have little or no field. Likewise regions inside the insulating jacket  302  have low field strength. The majority of the electromagnetic field strength is distributed in the lobes  304  at the outer surface of the insulating jacket  302  and in close proximity thereof. The presence of a non-circular and non-fundamental guided wave mode is shown by the high electromagnetic field strengths at the top and bottom of the outer surface of the insulating jacket  302  (in the orientation of the diagram)—as opposed to very small field strengths on the other sides of the insulating jacket  302 . 
     The example shown corresponds to a 38 GHz electromagnetic wave guided by a wire with a diameter of 1.1 cm and a dielectric insulation of thickness of 0.36 cm. Because the electromagnetic wave is guided by the transmission medium  125  and the majority of the field strength is concentrated in the air outside of the insulating jacket  302  within a limited distance of the outer surface, the guided wave can propagate longitudinally down the transmission medium  125  with very low loss. In the example shown, this “limited distance” corresponds to a distance from the outer surface that is less than half the largest cross sectional dimension of the transmission medium  125 . In this case, the largest cross sectional dimension of the wire corresponds to the overall diameter of 1.82 cm, however, this value can vary with the size and shape of the transmission medium  125 . For example, should the transmission medium  125  be of a rectangular shape with a height of 0.3 cm and a width of 0.4 cm, the largest cross sectional dimension would be the diagonal of 0.5 cm and the corresponding limited distance would be 0.25 cm. The dimensions of the area containing the majority of the field strength also vary with the frequency, and in general, increase as carrier frequencies decrease. 
     It should also be noted that the components of a guided wave communication system, such as couplers and transmission media can have their own cut-off frequencies for each guided wave mode. The cut-off frequency generally sets forth the lowest frequency that a particular guided wave mode is designed to be supported by that particular component. In an example embodiment, the particular non-circular and non-fundamental mode of propagation shown is induced on the transmission medium  125  by an electromagnetic wave having a frequency that falls within a limited range (such as Fc to 2Fc) of the cut-off frequency Fc for this particular non-fundamental mode. The cut-off frequency Fc is particular to the characteristics of transmission medium  125 . For embodiments as shown that include an inner conductor  301  surrounded by an insulating jacket  302 , this cutoff frequency can vary based on the dimensions and properties of the insulating jacket  302  and potentially the dimensions and properties of the inner conductor  301  and can be determined experimentally to have a desired mode pattern. It should be noted however, that similar effects can be found for a hollow dielectric or insulator without an inner conductor or conductive shield. In this case, the cutoff frequency can vary based on the dimensions and properties of the hollow dielectric or insulator. 
     At frequencies lower than the cut-off frequency, the non-circular mode is difficult to induce in the transmission medium  125  and fails to propagate for all but trivial distances. As the frequency increases above the limited range of frequencies about the cut-off frequency, the non-circular mode shifts more and more inward of the insulating jacket  302 . At frequencies much larger than the cut-off frequency, the field strength is no longer concentrated outside of the insulating jacket, but primarily inside of the insulating jacket  302 . While the transmission medium  125  provides strong guidance to the electromagnetic wave and propagation is still possible, ranges are more limited by increased losses due to propagation within the insulating jacket  302 —as opposed to the surrounding air. 
     Referring now to  FIG. 4 , a graphical diagram  400  illustrating an example, non-limiting embodiment of an electromagnetic field distribution is shown. In particular, a cross section diagram  400 , similar to  FIG. 3  is shown with common reference numerals used to refer to similar elements. The example shown corresponds to a 60 GHz wave guided by a wire with a diameter of 1.1 cm and a dielectric insulation of thickness of 0.36 cm. Because the frequency of the guided wave is above the limited range of the cut-off frequency of this particular non-fundamental mode, much of the field strength has shifted inward of the insulating jacket  302 . In particular, the field strength is concentrated primarily inside of the insulating jacket  302 . While the transmission medium  125  provides strong guidance to the electromagnetic wave and propagation is still possible, ranges are more limited when compared with the embodiment of  FIG. 3 , by increased losses due to propagation within the insulating jacket  302 . 
     Referring now to  FIG. 5A , a graphical diagram illustrating an example, non-limiting embodiment of a frequency response is shown. In particular, diagram  500  presents a graph of end-to-end loss (in dB) as a function of frequency, overlaid with electromagnetic field distributions  510 ,  520  and  530  at three points for a 200 cm insulated medium voltage wire. The boundary between the insulator and the surrounding air is represented by reference numeral  525  in each electromagnetic field distribution. 
     As discussed in conjunction with  FIG. 3 , an example of a desired non-circular mode of propagation shown is induced on the transmission medium  125  by an electromagnetic wave having a frequency that falls within a limited range (such as Fc to 2Fc) of the lower cut-off frequency Fc of the transmission medium for this particular non-circular mode. In particular, the electromagnetic field distribution  520  at 6 GHz falls within this modal “sweet spot” that enhances electromagnetic wave propagation along an insulated transmission medium and reduces end-to-end transmission loss. In this particular mode, guided waves are partially embedded in the insulator and partially radiating on the outer surface of the insulator. In this fashion, the electromagnetic waves are “lightly” coupled to the insulator so as to enable guided electromagnetic wave propagation at long distances with low propagation loss. 
     At lower frequencies represented by the electromagnetic field distribution  510  at 3 GHz, the non-circular mode radiates more heavily generating higher propagation losses. At higher frequencies represented by the electromagnetic field distribution  530  at 9 GHz, the non-circular mode shifts more and more inward of the insulating jacket providing too much absorption, again generating higher propagation losses. 
     Referring now to  FIG. 5B , a graphical diagram  550  illustrating example, non-limiting embodiments of a longitudinal cross-section of a transmission medium  125 , such as an insulated wire, depicting fields of guided electromagnetic waves at various operating frequencies is shown. As shown in diagram  556 , when the guided electromagnetic waves are at approximately the cutoff frequency (f c ) corresponding to the modal “sweet spot”, the guided electromagnetic waves are loosely coupled to the insulated wire so that absorption is reduced, and the fields of the guided electromagnetic waves are bound sufficiently to reduce the amount radiated into the environment (e.g., air). Because absorption and radiation of the fields of the guided electromagnetic waves is low, propagation losses are consequently low, enabling the guided electromagnetic waves to propagate for longer distances. 
     As shown in diagram  554 , propagation losses increase when an operating frequency of the guide electromagnetic waves increases above about two-times the cutoff frequency (f c )—or as referred to, above the range of the “sweet spot”. More of the field strength of the electromagnetic wave is driven inside the insulating layer, increasing propagation losses. At frequencies much higher than the cutoff frequency (f c ) the guided electromagnetic waves are strongly bound to the insulated wire as a result of the fields emitted by the guided electromagnetic waves being concentrated in the insulation layer of the wire, as shown in diagram  552 . This in turn raises propagation losses further due to absorption of the guided electromagnetic waves by the insulation layer. Similarly, propagation losses increase when the operating frequency of the guided electromagnetic waves is substantially below the cutoff frequency (f c ), as shown in diagram  558 . At frequencies much lower than the cutoff frequency (f c ) the guided electromagnetic waves are weakly (or nominally) bound to the insulated wire and thereby tend to radiate into the environment (e.g., air), which in turn, raises propagation losses due to radiation of the guided electromagnetic waves. 
     Referring now to  FIG. 6 , a graphical diagram  600  illustrating an example, non-limiting embodiment of an electromagnetic field distribution is shown. In this embodiment, a transmission medium  602  is a bare wire, as shown in cross section. The diagram  600  includes different gray-scales that represent differing electromagnetic field strengths generated by the propagation of a guided wave having a symmetrical and fundamental TM00 guided wave mode at a single carrier frequency. 
     In this particular mode, electromagnetic waves are guided by the transmission medium  602  to propagate along an outer surface of the transmission medium—in this case, the outer surface of the bare wire. Electromagnetic waves are “lightly” coupled to the wire so as to enable electromagnetic wave propagation at long distances with low propagation loss. As shown, the guided wave has a field structure that lies substantially outside of the transmission medium  602  that serves to guide the electromagnetic waves. The regions inside the conductor of the transmission medium  602  have little or no field strength. 
     Referring now to  FIG. 7 , a block diagram  700  illustrating an example, non-limiting embodiment of an arc coupler is shown. In particular a coupling device is presented for use in a transmission device, such as transmission device  101  or  102  presented in conjunction with  FIG. 1 . The coupling device includes an arc coupler  704  coupled to a transmitter circuit  712  and termination or damper  714 . The arc coupler  704  can be made of a dielectric material, or other low-loss insulator (e.g., Teflon, polyethylene, etc.), or made of a conducting (e.g., metallic, non-metallic, etc.) material, or any combination of the foregoing materials. As shown, the arc coupler  704  operates as a waveguide and has a wave  706  propagating as a guided wave, within and about a waveguide surface of the arc coupler  704 . In the embodiment shown, at least a portion of the arc coupler  704  can be placed near a wire  702  or other transmission medium, (such as transmission medium  125 ), in order to facilitate coupling between the arc coupler  704  and the wire  702  or other transmission medium, as described herein to launch the guided wave  708  on the wire. The arc coupler  704  can be placed such that a portion of the curved arc coupler  704  is tangential to, and parallel or substantially parallel to the wire  702 . The portion of the arc coupler  704  that is parallel to the wire can be an apex of the curve, or any point where a tangent of the curve is parallel to the wire  702 . When the arc coupler  704  is positioned or placed thusly, the wave  706  travelling along the arc coupler  704  couples, at least in part, to the wire  702 , and propagates as guided wave  708  around or about the wire surface of the wire  702  and longitudinally along the wire  702 . The guided wave  708  can be characterized as a surface wave or other electromagnetic wave that is guided by or bound to the wire  702  or other transmission medium. 
     A portion of the wave  706  that does not couple to the wire  702  propagates as a wave  710  along the arc coupler  704 . It will be appreciated that the arc coupler  704  can be configured and arranged in a variety of positions in relation to the wire  702  to achieve a desired level of coupling or non-coupling of the wave  706  to the wire  702 . For example, the curvature and/or length of the arc coupler  704  that is parallel or substantially parallel, as well as its separation distance (which can include zero separation distance in an embodiment), to the wire  702  can be varied without departing from example embodiments. Likewise, the arrangement of arc coupler  704  in relation to the wire  702  may be varied based upon considerations of the respective intrinsic characteristics (e.g., thickness, composition, electromagnetic properties, etc.) of the wire  702  and the arc coupler  704 , as well as the characteristics (e.g., frequency, energy level, etc.) of the waves  706  and  708 . 
     The guided wave  708  stays parallel or substantially parallel to the wire  702 , even as the wire  702  bends and flexes. Bends in the wire  702  can increase transmission losses, which are also dependent on wire diameters, frequency, and materials. If the dimensions of the arc coupler  704  are chosen for efficient power transfer, most of the power in the wave  706  is transferred to the wire  702 , with little power remaining in wave  710 . It will be appreciated that the guided wave  708  can still be multi-modal in nature (discussed herein), including having modes that are non-circular, non-fundamental and/or asymmetric, while traveling along a path that is parallel or substantially parallel to the wire  702 , with or without a fundamental transmission mode. In an embodiment, non-circular, non-fundamental and/or asymmetric modes can be utilized to minimize transmission losses and/or obtain increased propagation distances. 
     It is noted that the term “parallel” is generally a geometric construct which often is not exactly achievable in real systems. Accordingly, the term “parallel” as utilized in the subject disclosure represents an approximation rather than an exact configuration when used to describe embodiments disclosed in the subject disclosure. In an embodiment, “substantially parallel” can include approximations that are within 30 degrees of true parallel in all dimensions. 
     In an embodiment, the wave  706  can exhibit one or more wave propagation modes. The arc coupler modes can be dependent on the shape and/or design of the coupler  704 . The one or more arc coupler modes of wave  706  can generate, influence, or impact one or more wave propagation modes of the guided wave  708  propagating along wire  702 . It should be particularly noted however that the guided wave modes present in the guided wave  706  may be the same or different from the guided wave modes of the guided wave  708 . In this fashion, one or more guided wave modes of the guided wave  706  may not be transferred to the guided wave  708 , and further one or more guided wave modes of guided wave  708  may not have been present in guided wave  706 . It should also be noted that the cut-off frequency of the arc coupler  704  for a particular guided wave mode may be different than the cutoff frequency of the wire  702  or other transmission medium for that same mode. For example, while the wire  702  or other transmission medium may be operated slightly above its cutoff frequency for a particular guided wave mode, the arc coupler  704  may be operated well above its cut-off frequency for that same mode for low loss, slightly below its cut-off frequency for that same mode to, for example, induce greater coupling and power transfer, or some other point in relation to the arc coupler&#39;s cutoff frequency for that mode. 
     In an embodiment, the wave propagation modes on the wire  702  can be similar to the arc coupler modes since both waves  706  and  708  propagate about the outside of the arc coupler  704  and wire  702  respectively. In some embodiments, as the wave  706  couples to the wire  702 , the modes can change form, or new modes can be created or generated, due to the coupling between the arc coupler  704  and the wire  702 . For example, differences in size, material, and/or impedances of the arc coupler  704  and wire  702  may create additional modes not present in the arc coupler modes and/or suppress some of the arc coupler modes. The wave propagation modes can comprise the fundamental transverse magnetic mode (TM 00 ), where only small magnetic fields extend in the direction of propagation, and the electric field extends radially outwards and then longitudinally while the guided wave propagates along the wire. This guided wave mode can be donut shaped, where only a portion of the electromagnetic fields exist within the arc coupler  704  or wire  702 . 
     While the waves  706  and  708  can comprise a fundamental TM mode, the waves  706  and  708 , also or in the alternative, can comprise non-fundamental TM modes. While particular wave propagation modes are discussed above, other wave propagation modes in or along the coupler and/or along the wire are likewise possible such as transverse electric (TE) and hybrid (EH or HE) modes, based on the frequencies employed, the design of the arc coupler  704 , the dimensions and composition of the wire  702 , as well as its surface characteristics, its insulation if present, the electromagnetic properties of the surrounding environment, etc. It should be noted that, depending on the frequency, the electrical and physical characteristics of the wire  702  and the particular wave propagation modes that are generated, guided wave  708  can travel along the conductive surface of an oxidized uninsulated wire, an unoxidized uninsulated wire, an insulated wire and/or along the insulating surface of an insulated wire. 
     In an embodiment, a diameter of the arc coupler  704  is smaller than the diameter of the wire  702 . For the millimeter-band wavelength being used, the arc coupler  704  supports a single waveguide mode that makes up wave  706 . This single waveguide mode can change as it couples to the wire  702  as guided wave  708 . If the arc coupler  704  were larger, more than one waveguide mode can be supported, but these additional waveguide modes may not couple to the wire  702  as efficiently, and higher coupling losses can result. However, in some alternative embodiments, the diameter of the arc coupler  704  can be equal to or larger than the diameter of the wire  702 , for example, where higher coupling losses are desirable or when used in conjunction with other techniques to otherwise reduce coupling losses (e.g., impedance matching with tapering, etc.). 
     In an embodiment, the wavelength of the waves  706  and  708  are comparable in size, or smaller than a circumference of the arc coupler  704  and the wire  702 . In an example, if the wire  702  has a diameter of 0.5 cm, and a corresponding circumference of around 1.5 cm, the wavelength of the transmission is around 1.5 cm or less, corresponding to a frequency of 70 GHz or greater. In another embodiment, a suitable frequency of the transmission and the carrier-wave signal is in the range of 30-100 GHz, perhaps around 30-60 GHz, and around 38 GHz in one example. In an embodiment, when the circumference of the arc coupler  704  and wire  702  is comparable in size to, or greater, than a wavelength of the transmission, the waves  706  and  708  can exhibit multiple wave propagation modes including fundamental and/or non-fundamental (symmetric and/or asymmetric, circular and/or non-circular) modes that propagate over sufficient distances to support various communication systems described herein. The waves  706  and  708  can therefore comprise more than one type of electric and magnetic field configuration. In an embodiment, as the guided wave  708  propagates down the wire  702 , the electrical and magnetic field configurations will remain the same from end to end of the wire  702 . In other embodiments, as the guided wave  708  encounters interference (distortion or obstructions) or loses energy due to transmission losses or scattering, the electric and magnetic field configurations can change as the guided wave  708  propagates down wire  702 . 
     In an embodiment, the arc coupler  704  can be composed of nylon, Teflon, polyethylene, a polyamide, or other plastics. In other embodiments, other dielectric materials can be employed. The wire surface of wire  702  can be metallic with either a bare metallic surface, or can be insulated using plastic, dielectric, insulator or other coating, jacket or sheathing. In an embodiment, a dielectric or otherwise non-conducting/insulated waveguide can be paired with either a bare/metallic wire or insulated wire. In other embodiments, a metallic and/or conductive waveguide can be paired with a bare/metallic wire or insulated wire. In an embodiment, an oxidation layer on the bare metallic surface of the wire  702  (e.g., resulting from exposure of the bare metallic surface to oxygen/air) can also provide insulating or dielectric properties similar to those provided by some insulators or sheathings. 
     It is noted that the graphical representations of waves  706 ,  708  and  710  are presented merely to illustrate the principles that wave  706  induces or otherwise launches a guided wave  708  on a wire  702  that operates, for example, as a single wire transmission line. Wave  710  represents the portion of wave  706  that remains on the arc coupler  704  after the generation of guided wave  708 . The actual electric and magnetic fields generated as a result of such wave propagation may vary depending on the frequencies employed, the particular wave propagation mode or modes, the design of the arc coupler  704 , the dimensions and composition of the wire  702 , as well as its surface characteristics, its optional insulation, the electromagnetic properties of the surrounding environment, etc. 
     It is noted that arc coupler  704  can include a termination circuit or damper  714  at the end of the arc coupler  704  that can absorb leftover radiation or energy from wave  710 . The termination circuit or damper  714  can prevent and/or minimize the leftover radiation or energy from wave  710  reflecting back toward transmitter circuit  712 . In an embodiment, the termination circuit or damper  714  can include termination resistors, absorbing materials and/or other components that perform impedance matching to attenuate reflection. In some embodiments, if the coupling efficiencies are high enough, and/or wave  710  is sufficiently small, it may not be necessary to use a termination circuit or damper  714 . For the sake of simplicity, these transmitter  712  and termination circuits or dampers  714  may not be depicted in the other figures, but in those embodiments, transmitter and termination circuits or dampers may possibly be used. 
     Further, while a single arc coupler  704  is presented that generates a single guided wave  708 , multiple arc couplers  704  placed at different points along the wire  702  and/or at different azimuthal orientations about the wire can be employed to generate and receive multiple guided waves  708  at the same or different frequencies, at the same or different phases, at the same or different wave propagation modes. 
       FIG. 8 , a block diagram  800  illustrating an example, non-limiting embodiment of an arc coupler is shown. In the embodiment shown, at least a portion of the coupler  704  can be placed near a wire  702  or other transmission medium, (such as transmission medium  125 ), in order to facilitate coupling between the arc coupler  704  and the wire  702  or other transmission medium, to extract a portion of the guided wave  806  as a guided wave  808  as described herein. The arc coupler  704  can be placed such that a portion of the curved arc coupler  704  is tangential to, and parallel or substantially parallel to the wire  702 . The portion of the arc coupler  704  that is parallel to the wire can be an apex of the curve, or any point where a tangent of the curve is parallel to the wire  702 . When the arc coupler  704  is positioned or placed thusly, the wave  806  travelling along the wire  702  couples, at least in part, to the arc coupler  704 , and propagates as guided wave  808  along the arc coupler  704  to a receiving device (not expressly shown). A portion of the wave  806  that does not couple to the arc coupler propagates as wave  810  along the wire  702  or other transmission medium. 
     In an embodiment, the wave  806  can exhibit one or more wave propagation modes. The arc coupler modes can be dependent on the shape and/or design of the coupler  704 . The one or more modes of guided wave  806  can generate, influence, or impact one or more guide-wave modes of the guided wave  808  propagating along the arc coupler  704 . It should be particularly noted however that the guided wave modes present in the guided wave  806  may be the same or different from the guided wave modes of the guided wave  808 . In this fashion, one or more guided wave modes of the guided wave  806  may not be transferred to the guided wave  808 , and further one or more guided wave modes of guided wave  808  may not have been present in guided wave  806 . 
     Referring now to  FIG. 9A , a block diagram  900  illustrating an example, non-limiting embodiment of a stub coupler is shown. In particular a coupling device that includes stub coupler  904  is presented for use in a transmission device, such as transmission device  101  or  102  presented in conjunction with  FIG. 1 . The stub coupler  904  can be made of a dielectric material, or other low-loss insulator (e.g., Teflon, polyethylene and etc.), or made of a conducting (e.g., metallic, non-metallic, etc.) material, or any combination of the foregoing materials. As shown, the stub coupler  904  operates as a waveguide and has a wave  906  propagating as a guided wave within and about a waveguide surface of the stub coupler  904 . In the embodiment shown, at least a portion of the stub coupler  904  can be placed near a wire  702  or other transmission medium, (such as transmission medium  125 ), in order to facilitate coupling between the stub coupler  904  and the wire  702  or other transmission medium, as described herein to launch the guided wave  908  on the wire. 
     In an embodiment, the stub coupler  904  is curved, and an end of the stub coupler  904  can be tied, fastened, or otherwise mechanically coupled to a wire  702 . When the end of the stub coupler  904  is fastened to the wire  702 , the end of the stub coupler  904  is parallel or substantially parallel to the wire  702 . Alternatively, another portion of the dielectric waveguide beyond an end can be fastened or coupled to wire  702  such that the fastened or coupled portion is parallel or substantially parallel to the wire  702 . The fastener  910  can be a nylon cable tie or other type of non-conducting/dielectric material that is either separate from the stub coupler  904  or constructed as an integrated component of the stub coupler  904 . The stub coupler  904  can be adjacent to the wire  702  without surrounding the wire  702 . 
     Like the arc coupler  704  described in conjunction with  FIG. 7 , when the stub coupler  904  is placed with the end parallel to the wire  702 , the guided wave  906  travelling along the stub coupler  904  couples to the wire  702 , and propagates as guided wave  908  about the wire surface of the wire  702 . In an example embodiment, the guided wave  908  can be characterized as a surface wave or other electromagnetic wave. 
     It is noted that the graphical representations of waves  906  and  908  are presented merely to illustrate the principles that wave  906  induces or otherwise launches a guided wave  908  on a wire  702  that operates, for example, as a single wire transmission line. The actual electric and magnetic fields generated as a result of such wave propagation may vary depending on one or more of the shape and/or design of the coupler, the relative position of the dielectric waveguide to the wire, the frequencies employed, the design of the stub coupler  904 , the dimensions and composition of the wire  702 , as well as its surface characteristics, its optional insulation, the electromagnetic properties of the surrounding environment, etc. 
     In an embodiment, an end of stub coupler  904  can taper towards the wire  702  in order to increase coupling efficiencies. Indeed, the tapering of the end of the stub coupler  904  can provide impedance matching to the wire  702  and reduce reflections, according to an example embodiment of the subject disclosure. For example, an end of the stub coupler  904  can be gradually tapered in order to obtain a desired level of coupling between waves  906  and  908  as illustrated in  FIG. 9A . 
     In an embodiment, the fastener  910  can be placed such that there is a short length of the stub coupler  904  between the fastener  910  and an end of the stub coupler  904 . Maximum coupling efficiencies are realized in this embodiment when the length of the end of the stub coupler  904  that is beyond the fastener  910  is at least several wavelengths long for whatever frequency is being transmitted. 
     Turning now to  FIG. 9B , a diagram  950  illustrating an example, non-limiting embodiment of an electromagnetic distribution in accordance with various aspects described herein is shown. In particular, an electromagnetic distribution is presented in two dimensions for a transmission device that includes coupler  952 , shown in an example stub coupler constructed of a dielectric material. The coupler  952  couples an electromagnetic wave for propagation as a guided wave along an outer surface of a wire  702  or other transmission medium. 
     The coupler  952  guides the electromagnetic wave to a junction at x 0  via a symmetrical guided wave mode. While some of the energy of the electromagnetic wave that propagates along the coupler  952  is outside of the coupler  952 , the majority of the energy of this electromagnetic wave is contained within the coupler  952 . The junction at x 0  couples the electromagnetic wave to the wire  702  or other transmission medium at an azimuthal angle corresponding to the bottom of the transmission medium. This coupling induces an electromagnetic wave that is guided to propagate along the outer surface of the wire  702  or other transmission medium via at least one guided wave mode in direction  956 . The majority of the energy of the guided electromagnetic wave is outside or, but in close proximity to the outer surface of the wire  702  or other transmission medium. In the example shown, the junction at x 0  forms an electromagnetic wave that propagates via both a fundamental TM00 mode and at least one non-fundamental mode, such as the first order mode presented in conjunction with  FIG. 3 , that skims the surface of the wire  702  or other transmission medium. 
     It is noted that the graphical representations of guided waves are presented merely to illustrate an example of guided wave coupling and propagation. The actual electric and magnetic fields generated as a result of such wave propagation may vary depending on the frequencies employed, the design and/or configuration of the coupler  952 , the dimensions and composition of the wire  702  or other transmission medium, as well as its surface characteristics, its insulation if present, the electromagnetic properties of the surrounding environment, etc. 
     Turning now to  FIG. 10 , illustrated is a block diagram  1000  of an example, non-limiting embodiment of a coupler and transceiver system in accordance with various aspects described herein. The system is an example of transmission device  101  or  102 . In particular, the communications interface  1008  is an example of communications interface  205 , the stub coupler  1002  is an example of coupler  220 , and the transmitter/receiver device  1006 , diplexer  1016 , power amplifier  1014 , low noise amplifier  1018 , frequency mixers  1010  and  1020  and local oscillator  1012  collectively form an example of transceiver  210 . 
     In operation, the transmitter/receiver device  1006  launches and receives waves (e.g., guided wave  1004  onto stub coupler  1002 ). The guided waves  1004  can be used to transport signals received from and sent to a host device, base station, mobile devices, a building or other device by way of a communications interface  1008 . The communications interface  1008  can be an integral part of system  1000 . Alternatively, the communications interface  1008  can be tethered to system  1000 . The communications interface  1008  can comprise a wireless interface for interfacing to the host device, base station, mobile devices, a building or other device utilizing any of various present or future wireless signaling protocols (e.g., LTE, WiFi, WiMAX, IEEE 802.xx, 5G, etc.) including an infrared protocol such as an infrared data association (IrDA) protocol or other line of sight optical protocol. The communications interface  1008  can also comprise a wired interface such as a fiber optic line, coaxial cable, twisted pair, category 5 (CAT-5) cable or other suitable wired or optical mediums for communicating with the host device, base station, mobile devices, a building or other device via a protocol such as an Ethernet protocol, universal serial bus (USB) protocol, a data over cable service interface specification (DOCSIS) protocol, a digital subscriber line (DSL) protocol, a Firewire (IEEE 1394) protocol, or other wired or optical protocol. For embodiments where system  1000  functions as a repeater, the communications interface  1008  may not be necessary. 
     The output signals (e.g., Tx) of the communications interface  1008  can be combined with a carrier wave (e.g., millimeter-wave carrier wave) generated by a local oscillator  1012  at frequency mixer  1010 . Frequency mixer  1010  can use heterodyning techniques or other frequency shifting techniques to frequency shift the output signals from communications interface  1008 . For example, signals sent to and from the communications interface  1008  can be modulated signals such as orthogonal frequency division multiplexed (OFDM) signals formatted in accordance with a Long-Term Evolution (LTE) wireless protocol or other wireless 3G, 4G, 5G or higher voice and data protocol, a Zigbee®, WIMAX, UltraWideband or IEEE 802.11 wireless protocol; a wired protocol such as an Ethernet protocol, universal serial bus (USB) protocol, a data over cable service interface specification (DOCSIS) protocol, a digital subscriber line (DSL) protocol, a Firewire (IEEE 1394) protocol or other wired or wireless protocol. In an example embodiment, this frequency conversion can be done in the analog domain, and as a result, the frequency shifting can be done without regard to the type of communications protocol used by a base station, mobile devices, or in-building devices. As new communications technologies are developed, the communications interface  1008  can be upgraded (e.g., updated with software, firmware, and/or hardware) or replaced and the frequency shifting and transmission apparatus can remain, simplifying upgrades. The carrier wave can then be sent to a power amplifier (“PA”)  1014  and can be transmitted via the transmitter receiver device  1006  via the diplexer  1016 . 
     Signals received from the transmitter/receiver device  1006  that are directed towards the communications interface  1008  can be separated from other signals via diplexer  1016 . The received signal can then be sent to low noise amplifier (“LNA”)  1018  for amplification. A frequency mixer  1020 , with help from local oscillator  1012  can downshift the received signal (which is in the millimeter-wave band or around 38 GHz in some embodiments) to the native frequency. The communications interface  1008  can then receive the transmission at an input port (Rx). 
     In an embodiment, transmitter/receiver device  1006  can include a cylindrical or non-cylindrical metal (which, for example, can be hollow in an embodiment, but not necessarily drawn to scale) or other conducting or non-conducting waveguide and an end of the stub coupler  1002  can be placed in or in proximity to the waveguide or the transmitter/receiver device  1006  such that when the transmitter/receiver device  1006  generates a transmission, the guided wave couples to stub coupler  1002  and propagates as a guided wave  1004  about the waveguide surface of the stub coupler  1002 . In some embodiments, the guided wave  1004  can propagate in part on the outer surface of the stub coupler  1002  and in part inside the stub coupler  1002 . In other embodiments, the guided wave  1004  can propagate substantially or completely on the outer surface of the stub coupler  1002 . In yet other embodiments, the guided wave  1004  can propagate substantially or completely inside the stub coupler  1002 . In this latter embodiment, the guided wave  1004  can radiate at an end of the stub coupler  1002  (such as the tapered end shown in  FIG. 4 ) for coupling to a transmission medium such as a wire  702  of  FIG. 7 . Similarly, if guided wave  1004  is incoming (coupled to the stub coupler  1002  from a wire  702 ), guided wave  1004  then enters the transmitter/receiver device  1006  and couples to the cylindrical waveguide or conducting waveguide. While transmitter/receiver device  1006  is shown to include a separate waveguide—an antenna, cavity resonator, klystron, magnetron, travelling wave tube, or other radiating element can be employed to induce a guided wave on the coupler  1002 , with or without the separate waveguide. 
     In an embodiment, stub coupler  1002  can be wholly constructed of a dielectric material (or another suitable insulating material), without any metallic or otherwise conducting materials therein. Stub coupler  1002  can be composed of nylon, Teflon, polyethylene, a polyamide, other plastics, or other materials that are non-conducting and suitable for facilitating transmission of electromagnetic waves at least in part on an outer surface of such materials. In another embodiment, stub coupler  1002  can include a core that is conducting/metallic, and have an exterior dielectric surface. Similarly, a transmission medium that couples to the stub coupler  1002  for propagating electromagnetic waves induced by the stub coupler  1002  or for supplying electromagnetic waves to the stub coupler  1002  can, in addition to being a bare or insulated wire, be wholly constructed of a dielectric material (or another suitable insulating material), without any metallic or otherwise conducting materials therein. 
     It is noted that although  FIG. 10  shows that the opening of transmitter receiver device  1006  is much wider than the stub coupler  1002 , this is not to scale, and that in other embodiments the width of the stub coupler  1002  is comparable or slightly smaller than the opening of the hollow waveguide. It is also not shown, but in an embodiment, an end of the coupler  1002  that is inserted into the transmitter/receiver device  1006  tapers down in order to reduce reflection and increase coupling efficiencies. The stub coupler  1002  can be representative of the arch coupler  704  of  FIGS. 7 and 8 , the stub coupler  904  of  FIG. 9A , the coupler  952 , or any other couplers described in the subject disclosure. 
     Before coupling to the stub coupler  1002 , the one or more waveguide modes of the guided wave generated by the transmitter/receiver device  1006  can couple to the stub coupler  1002  to induce one or more wave propagation modes of the guided wave  1004 . The wave propagation modes of the guided wave  1004  can be different than the hollow metal waveguide modes due to the different characteristics of the hollow metal waveguide and the dielectric waveguide. For instance, wave propagation modes of the guided wave  1004  can comprise the fundamental transverse magnetic mode (TM 00 ), where only small magnetic fields extend in the direction of propagation, HE11 or other modes supported by the stub coupler  1002  that generate one or more desired wave modes on the transmission medium. The fundamental transverse electromagnetic mode wave propagation mode may or may not exist inside a waveguide that is hollow. Therefore, the hollow metal waveguide modes that are used by transmitter/receiver device  1006  are waveguide modes, such as TE01 or TE11, that can propagate inside a circular, rectangular or other hollow metallic waveguide and couple effectively and efficiently to wave propagation modes of stub coupler  1002 . 
     It will be appreciated that other constructs or combinations of the transmitter/receiver device  1006  and stub coupler  1002  are possible. 
     Referring now to  FIG. 11 , a block diagram  1100  illustrating an example, non-limiting embodiment of a dual stub coupler is shown. In particular, a dual coupler design is presented for use in a transmission device, such as transmission device  101  or  102  presented in conjunction with  FIG. 1 . In an embodiment, two or more couplers (such as the stub couplers  1104  and  1106 ) can be positioned around a wire  1102  in order to receive guided wave  1108 . In an embodiment, one coupler is enough to receive the guided wave  1108 . In that case, guided wave  1108  couples to coupler  1104  and propagates as guided wave  1110 . If the field structure of the guided wave  1108  oscillates or undulates around the wire  1102  due to the particular guided wave mode(s) or various outside factors, then coupler  1106  can be placed such that guided wave  1108  couples to coupler  1106 . In some embodiments, four or more couplers can be placed around a portion of the wire  1102 , e.g., at 90 degrees or another spacing with respect to each other, in order to receive guided waves that may oscillate or rotate around the wire  1102 , that have been induced at different azimuthal orientations or that have non-fundamental or higher order modes that, for example, have lobes and/or nulls or other asymmetries that are orientation dependent. However, it will be appreciated that there may be less than or more than four couplers placed around a portion of the wire  1102  without departing from example embodiments. 
     It should be noted that while couplers  1106  and  1104  are illustrated as stub couplers, any other of the coupler designs described herein including arc couplers, antenna or horn couplers, magnetic couplers, etc., could likewise be used. It will also be appreciated that while some example embodiments have presented a plurality of couplers around at least a portion of a wire  1102 , this plurality of couplers can also be considered as part of a single coupler system having multiple coupler subcomponents. For example, two or more couplers can be manufactured as single system that can be installed around a wire in a single installation such that the couplers are either pre-positioned or adjustable relative to each other (either manually or automatically with a controllable mechanism such as a motor or other actuator) in accordance with the single system. 
     Receivers coupled to couplers  1106  and  1104  can use diversity combining to combine signals received from both couplers  1106  and  1104  in order to maximize the signal quality. In other embodiments, if one or the other of the couplers  1104  and  1106  receive a transmission that is above a predetermined threshold, receivers can use selection diversity when deciding which signal to use. Further, while reception by a plurality of couplers  1106  and  1104  is illustrated, transmission by couplers  1106  and  1104  in the same configuration can likewise take place. In particular, a wide range of multi-input multi-output (MIMO) transmission and reception techniques can be employed for transmissions where a transmission device, such as transmission device  101  or  102  presented in conjunction with  FIG. 1  includes multiple transceivers and multiple couplers. For example, such MIMO transmission and reception techniques include precoding, spatial multiplexing, diversity coding and guided wave mode division multiplexing applied to transmission and reception by multiple couplers/launchers that operate on a transmission medium with one or more surfaces that support guided wave communications. 
     It is noted that the graphical representations of waves  1108  and  1110  are presented merely to illustrate the principles that guided wave  1108  induces or otherwise launches a wave  1110  on a coupler  1104 . The actual electric and magnetic fields generated as a result of such wave propagation may vary depending on the frequencies employed, the design of the coupler  1104 , the dimensions and composition of the wire  1102 , as well as its surface characteristics, its insulation if any, the electromagnetic properties of the surrounding environment, etc. 
     Referring now to  FIG. 12 , a block diagram  1200  illustrating an example, non-limiting embodiment of a repeater system is shown. In particular, a repeater device  1210  is presented for use in a transmission device, such as transmission device  101  or  102  presented in conjunction with  FIG. 1 . In this system, two couplers  1204  and  1214  can be placed near a wire  1202  or other transmission medium such that guided waves  1205  propagating along the wire  1202  are extracted by coupler  1204  as wave  1206  (e.g. as a guided wave), and then are boosted or repeated by repeater device  1210  and launched as a wave  1216  (e.g. as a guided wave) onto coupler  1214 . The wave  1216  can then be launched on the wire  1202  and continue to propagate along the wire  1202  as a guided wave  1217 . In an embodiment, the repeater device  1210  can receive at least a portion of the power utilized for boosting or repeating through magnetic coupling with the wire  1202 , for example, when the wire  1202  is a power line or otherwise contains a power-carrying conductor. It should be noted that while couplers  1204  and  1214  are illustrated as stub couplers, any other of the coupler designs described herein including arc couplers, antenna or horn couplers, magnetic couplers, or the like, could likewise be used. 
     In some embodiments, repeater device  1210  can repeat the transmission associated with wave  1206 , and in other embodiments, repeater device  1210  can include a communications interface  205  that extracts data or other signals from the wave  1206  for supplying such data or signals to another network and/or one or more other devices as communication signals  110  or  112  and/or receiving communication signals  110  or  112  from another network and/or one or more other devices and launch guided wave  1216  having embedded therein the received communication signals  110  or  112 . In a repeater configuration, receiver waveguide  1208  can receive the wave  1206  from the coupler  1204  and transmitter waveguide  1212  can launch guided wave  1216  onto coupler  1214  as guided wave  1217 . Between receiver waveguide  1208  and transmitter waveguide  1212 , the signal embedded in guided wave  1206  and/or the guided wave  1216  itself can be amplified to correct for signal loss and other inefficiencies associated with guided wave communications or the signal can be received and processed to extract the data contained therein and regenerated for transmission. In an embodiment, the receiver waveguide  1208  can be configured to extract data from the signal, process the data to correct for data errors utilizing for example error correcting codes, and regenerate an updated signal with the corrected data. The transmitter waveguide  1212  can then transmit guided wave  1216  with the updated signal embedded therein. In an embodiment, a signal embedded in guided wave  1206  can be extracted from the transmission and processed for communication with another network and/or one or more other devices via communications interface  205  as communication signals  110  or  112 . Similarly, communication signals  110  or  112  received by the communications interface  205  can be inserted into a transmission of guided wave  1216  that is generated and launched onto coupler  1214  by transmitter waveguide  1212 . 
     It is noted that although  FIG. 12  shows guided wave transmissions  1206  and  1216  entering from the left and exiting to the right respectively, this is merely a simplification and is not intended to be limiting. In other embodiments, receiver waveguide  1208  and transmitter waveguide  1212  can also function as transmitters and receivers respectively, allowing the repeater device  1210  to be bi-directional. 
     In an embodiment, repeater device  1210  can be placed at locations where there are discontinuities or obstacles on the wire  1202  or other transmission medium. In the case where the wire  1202  is a power line, these obstacles can include transformers, connections, utility poles, and other such power line devices. The repeater device  1210  can help the guided (e.g., surface) waves jump over these obstacles on the line and boost the transmission power at the same time. In other embodiments, a coupler can be used to jump over the obstacle without the use of a repeater device. In that embodiment, both ends of the coupler can be tied or fastened to the wire, thus providing a path for the guided wave to travel without being blocked by the obstacle. 
     Turning now to  FIG. 13 , illustrated is a block diagram  1300  of an example, non-limiting embodiment of a bidirectional repeater in accordance with various aspects described herein. In particular, a bidirectional repeater device  1306  is presented for use in a transmission device, such as transmission device  101  or  102  presented in conjunction with  FIG. 1 . It should be noted that while the couplers are illustrated as stub couplers, any other of the coupler designs described herein including arc couplers, antenna or horn couplers, magnetic couplers, or the like, could likewise be used. The bidirectional repeater  1306  can employ diversity paths in the case of when two or more wires or other transmission media are present. Since guided wave transmissions have different transmission efficiencies and coupling efficiencies for transmission medium of different types such as insulated wires, un-insulated wires or other types of transmission media and further, if exposed to the elements, can be affected by weather, and other atmospheric conditions, it can be advantageous to selectively transmit on different transmission media at certain times. In various embodiments, the various transmission media can be designated as a primary, secondary, tertiary, etc. whether or not such designation indicates a preference of one transmission medium over another. 
     In the embodiment shown, the transmission media include an insulated or uninsulated wire  1302  and an insulated or uninsulated wire  1304  (referred to herein as wires  1302  and  1304 , respectively). The repeater device  1306  uses a receiver coupler  1308  to receive a guided wave traveling along wire  1302  and repeats the transmission using transmitter waveguide  1310  as a guided wave along wire  1304 . In other embodiments, repeater device  1306  can switch from the wire  1304  to the wire  1302 , or can repeat the transmissions along the same paths. Repeater device  1306  can include sensors, or be in communication with sensors (or a network management system  1601  depicted in  FIG. 16A ) that indicate conditions that can affect the transmission. Based on the feedback received from the sensors, the repeater device  1306  can make the determination about whether to keep the transmission along the same wire, or transfer the transmission to the other wire. 
     Turning now to  FIG. 14 , illustrated is a block diagram  1400  illustrating an example, non-limiting embodiment of a bidirectional repeater system. In particular, a bidirectional repeater system is presented for use in a transmission device, such as transmission device  101  or  102  presented in conjunction with  FIG. 1 . The bidirectional repeater system includes waveguide coupling devices  1402  and  1404  that receive and transmit transmissions from other coupling devices located in a distributed antenna system or backhaul system. 
     In various embodiments, waveguide coupling device  1402  can receive a transmission from another waveguide coupling device, wherein the transmission has a plurality of subcarriers. Diplexer  1406  can separate the transmission from other transmissions, and direct the transmission to low-noise amplifier (“LNA”)  1408 . A frequency mixer  1428 , with help from a local oscillator  1412 , can downshift the transmission (which is in the millimeter-wave band or around 38 GHz in some embodiments) to a lower frequency, such as a cellular band (˜1.9 GHz) for a distributed antenna system, a native frequency, or other frequency for a backhaul system. An extractor (or demultiplexer)  1432  can extract the signal on a subcarrier and direct the signal to an output component  1422  for optional amplification, buffering or isolation by power amplifier  1424  for coupling to communications interface  205 . The communications interface  205  can further process the signals received from the power amplifier  1424  or otherwise transmit such signals over a wireless or wired interface to other devices such as a base station, mobile devices, a building, etc. For the signals that are not being extracted at this location, extractor  1432  can redirect them to another frequency mixer  1436 , where the signals are used to modulate a carrier wave generated by local oscillator  1414 . The carrier wave, with its subcarriers, is directed to a power amplifier (“PA”)  1416  and is retransmitted by waveguide coupling device  1404  to another system, via diplexer  1420 . 
     An LNA  1426  can be used to amplify, buffer or isolate signals that are received by the communication interface  205  and then send the signal to a multiplexer  1434  which merges the signal with signals that have been received from waveguide coupling device  1404 . The signals received from coupling device  1404  have been split by diplexer  1420 , and then passed through LNA  1418 , and downshifted in frequency by frequency mixer  1438 . When the signals are combined by multiplexer  1434 , they are upshifted in frequency by frequency mixer  1430 , and then boosted by PA  1410 , and transmitted to another system by waveguide coupling device  1402 . In an embodiment bidirectional repeater system can be merely a repeater without the output device  1422 . In this embodiment, the multiplexer  1434  would not be utilized and signals from LNA  1418  would be directed to mixer  1430  as previously described. It will be appreciated that in some embodiments, the bidirectional repeater system could also be implemented using two distinct and separate unidirectional repeaters. In an alternative embodiment, a bidirectional repeater system could also be a booster or otherwise perform retransmissions without downshifting and upshifting. Indeed in example embodiment, the retransmissions can be based upon receiving a signal or guided wave and performing some signal or guided wave processing or reshaping, filtering, and/or amplification, prior to retransmission of the signal or guided wave. 
     Referring now to  FIG. 15 , a block diagram  1500  illustrating an example, non-limiting embodiment of a guided wave communications system is shown. This diagram depicts an exemplary environment in which a guided wave communication system, such as the guided wave communication system presented in conjunction with  FIG. 1 , can be used. 
     To provide network connectivity to additional base station devices, a backhaul network that links the communication cells (e.g., macrocells and macrocells) to network devices of a core network correspondingly expands. Similarly, to provide network connectivity to a distributed antenna system, an extended communication system that links base station devices and their distributed antennas is desirable. A guided wave communication system  1500  such as shown in  FIG. 15  can be provided to enable alternative, increased or additional network connectivity and a waveguide coupling system can be provided to transmit and/or receive guided wave (e.g., surface wave) communications on a transmission medium such as a wire that operates as a single-wire transmission line (e.g., a utility line), and that can be used as a waveguide and/or that otherwise operates to guide the transmission of an electromagnetic wave. 
     The guided wave communication system  1500  can comprise a first instance of a distribution system  1550  that includes one or more base station devices (e.g., base station device  1504 ) that are communicably coupled to a central office  1501  and/or a macrocell site  1502 . Base station device  1504  can be connected by a wired (e.g., fiber and/or cable), or by a wireless (e.g., microwave wireless) connection to the macrocell site  1502  and the central office  1501 . A second instance of the distribution system  1560  can be used to provide wireless voice and data services to mobile device  1522  and to residential and/or commercial establishments  1542  (herein referred to as establishments  1542 ). System  1500  can have additional instances of the distribution systems  1550  and  1560  for providing voice and/or data services to mobile devices  1522 - 1524  and establishments  1542  as shown in  FIG. 15 . 
     Macrocells such as macrocell site  1502  can have dedicated connections to a mobile network and base station device  1504  or can share and/or otherwise use another connection. Central office  1501  can be used to distribute media content and/or provide internet service provider (ISP) services to mobile devices  1522 - 1524  and establishments  1542 . The central office  1501  can receive media content from a constellation of satellites  1530  (one of which is shown in  FIG. 15 ) or other sources of content, and distribute such content to mobile devices  1522 - 1524  and establishments  1542  via the first and second instances of the distribution system  1550  and  1560 . The central office  1501  can also be communicatively coupled to the Internet  1503  for providing internet data services to mobile devices  1522 - 1524  and establishments  1542 . 
     Base station device  1504  can be mounted on, or attached to, utility pole  1516 . In other embodiments, base station device  1504  can be near transformers and/or other locations situated nearby a power line. Base station device  1504  can facilitate connectivity to a mobile network for mobile devices  1522  and  1524 . Antennas  1512  and  1514 , mounted on or near utility poles  1518  and  1520 , respectively, can receive signals from base station device  1504  and transmit those signals to mobile devices  1522  and  1524  over a much wider area than if the antennas  1512  and  1514  were located at or near base station device  1504 . 
     It is noted that  FIG. 15  displays three utility poles, in each instance of the distribution systems  1550  and  1560 , with one base station device, for purposes of simplicity. In other embodiments, utility pole  1516  can have more base station devices, and more utility poles with distributed antennas and/or tethered connections to establishments  1542 . 
     A transmission device  1506 , such as transmission device  101  or  102  presented in conjunction with  FIG. 1 , can transmit a signal from base station device  1504  to antennas  1512  and  1514  via utility or power line(s) that connect the utility poles  1516 ,  1518 , and  1520 . To transmit the signal, radio source and/or transmission device  1506  upconverts the signal (e.g., via frequency mixing) from base station device  1504  or otherwise converts the signal from the base station device  1504  to a microwave band signal and the transmission device  1506  launches a microwave band wave that propagates as a guided wave traveling along the utility line or other wire as described in previous embodiments. At utility pole  1518 , another transmission device  1508  receives the guided wave (and optionally can amplify it as needed or desired or operate as a repeater to receive it and regenerate it) and sends it forward as a guided wave on the utility line or other wire. The transmission device  1508  can also extract a signal from the microwave band guided wave and shift it down in frequency or otherwise convert it to its original cellular band frequency (e.g., 1.9 GHz or other defined cellular frequency) or another cellular (or non-cellular) band frequency. An antenna  1512  can wireless transmit the downshifted signal to mobile device  1522 . The process can be repeated by transmission device  1510 , antenna  1514  and mobile device  1524 , as necessary or desirable. 
     Transmissions from mobile devices  1522  and  1524  can also be received by antennas  1512  and  1514  respectively. The transmission devices  1508  and  1510  can upshift or otherwise convert the cellular band signals to microwave band and transmit the signals as guided wave (e.g., surface wave or other electromagnetic wave) transmissions over the power line(s) to base station device  1504 . 
     Media content received by the central office  1501  can be supplied to the second instance of the distribution system  1560  via the base station device  1504  for distribution to mobile devices  1522  and establishments  1542 . The transmission device  1510  can be tethered to the establishments  1542  by one or more wired connections or a wireless interface. The one or more wired connections may include without limitation, a power line, a coaxial cable, a fiber cable, a twisted pair cable, a guided wave transmission medium or other suitable wired mediums for distribution of media content and/or for providing internet services. In an example embodiment, the wired connections from the transmission device  1510  can be communicatively coupled to one or more very high bit rate digital subscriber line (VDSL) modems located at one or more corresponding service area interfaces (SAIs—not shown) or pedestals, each SAI or pedestal providing services to a portion of the establishments  1542 . The VDSL modems can be used to selectively distribute media content and/or provide internet services to gateways (not shown) located in the establishments  1542 . The SAIs or pedestals can also be communicatively coupled to the establishments  1542  over a wired medium such as a power line, a coaxial cable, a fiber cable, a twisted pair cable, a guided wave transmission medium or other suitable wired mediums. In other example embodiments, the transmission device  1510  can be communicatively coupled directly to establishments  1542  without intermediate interfaces such as the SAIs or pedestals. 
     In another example embodiment, system  1500  can employ diversity paths, where two or more utility lines or other wires are strung between the utility poles  1516 ,  1518 , and  1520  (e.g., for example, two or more wires between poles  1516  and  1520 ) and redundant transmissions from base station/macrocell site  1502  are transmitted as guided waves down the surface of the utility lines or other wires. The utility lines or other wires can be either insulated or uninsulated, and depending on the environmental conditions that cause transmission losses, the coupling devices can selectively receive signals from the insulated or uninsulated utility lines or other wires. The selection can be based on measurements of the signal-to-noise ratio of the wires, or based on determined weather/environmental conditions (e.g., moisture detectors, weather forecasts, etc.). The use of diversity paths with system  1500  can enable alternate routing capabilities, load balancing, increased load handling, concurrent bi-directional or synchronous communications, spread spectrum communications, etc. 
     It is noted that the use of the transmission devices  1506 ,  1508 , and  1510  in  FIG. 15  are by way of example only, and that in other embodiments, other uses are possible. For instance, transmission devices can be used in a backhaul communication system, providing network connectivity to base station devices. Transmission devices  1506 ,  1508 , and  1510  can be used in many circumstances where it is desirable to transmit guided wave communications over a wire, whether insulated or not insulated. Transmission devices  1506 ,  1508 , and  1510  are improvements over other coupling devices due to no contact or limited physical and/or electrical contact with the wires that may carry high voltages. The transmission device can be located away from the wire (e.g., spaced apart from the wire) and/or located on the wire so long as it is not electrically in contact with the wire, as the dielectric acts as an insulator, allowing for cheap, easy, and/or less complex installation. However, as previously noted conducting or non-dielectric couplers can be employed, for example in configurations where the wires correspond to a telephone network, cable television network, broadband data service, fiber optic communications system or other network employing low voltages or having insulated transmission lines. 
     It is further noted, that while base station device  1504  and macrocell site  1502  are illustrated in an embodiment, other network configurations are likewise possible. For example, devices such as access points or other wireless gateways can be employed in a similar fashion to extend the reach of other networks such as a wireless local area network, a wireless personal area network or other wireless network that operates in accordance with a communication protocol such as a 802.11 protocol, WIMAX protocol, UltraWideband protocol, Bluetooth® protocol, Zigbee® protocol or other wireless protocol. 
     Referring now to  FIGS. 16A &amp; 16B , block diagrams illustrating an example, non-limiting embodiment of a system for managing a power grid communication system are shown. Considering  FIG. 16A , a waveguide system  1602  is presented for use in a guided wave communications system  1600 , such as the system presented in conjunction with  FIG. 15 . The waveguide system  1602  can comprise sensors  1604 , a power management system  1605 , a transmission device  101  or  102  that includes at least one communication interface  205 , transceiver  210  and coupler  220 . 
     The waveguide system  1602  can be coupled to a power line  1610  for facilitating guided wave communications in accordance with embodiments described in the subject disclosure. In an example embodiment, the transmission device  101  or  102  includes coupler  220  for inducing electromagnetic waves on a surface of the power line  1610  that longitudinally propagate along the surface of the power line  1610  as described in the subject disclosure. The transmission device  101  or  102  can also serve as a repeater for retransmitting electromagnetic waves on the same power line  1610  or for routing electromagnetic waves between power lines  1610  as shown in  FIGS. 12-13 . 
     The transmission device  101  or  102  includes transceiver  210  configured to, for example, up-convert a signal operating at an original frequency range to electromagnetic waves operating at, exhibiting, or associated with a carrier frequency that propagate along a coupler to induce corresponding guided electromagnetic waves that propagate along a surface of the power line  1610 . A carrier frequency can be represented by a center frequency having upper and lower cutoff frequencies that define the bandwidth of the electromagnetic waves. The power line  1610  can be a wire (e.g., single stranded or multi-stranded) having a conducting surface or insulated surface. The transceiver  210  can also receive signals from the coupler  220  and down-convert the electromagnetic waves operating at a carrier frequency to signals at their original frequency. 
     Signals received by the communications interface  205  of transmission device  101  or  102  for up-conversion can include without limitation signals supplied by a central office  1611  over a wired or wireless interface of the communications interface  205 , a base station  1614  over a wired or wireless interface of the communications interface  205 , wireless signals transmitted by mobile devices  1620  to the base station  1614  for delivery over the wired or wireless interface of the communications interface  205 , signals supplied by in-building communication devices  1618  over the wired or wireless interface of the communications interface  205 , and/or wireless signals supplied to the communications interface  205  by mobile devices  1612  roaming in a wireless communication range of the communications interface  205 . In embodiments where the waveguide system  1602  functions as a repeater, such as shown in  FIGS. 12-13 , the communications interface  205  may or may not be included in the waveguide system  1602 . 
     The electromagnetic waves propagating along the surface of the power line  1610  can be modulated and formatted to include packets or frames of data that include a data payload and further include networking information (such as header information for identifying one or more destination waveguide systems  1602 ). The networking information may be provided by the waveguide system  1602  or an originating device such as the central office  1611 , the base station  1614 , mobile devices  1620 , or in-building devices  1618 , or a combination thereof. Additionally, the modulated electromagnetic waves can include error correction data for mitigating signal disturbances. The networking information and error correction data can be used by a destination waveguide system  1602  for detecting transmissions directed to it, and for down-converting and processing with error correction data transmissions that include voice and/or data signals directed to recipient communication devices communicatively coupled to the destination waveguide system  1602 . 
     Referring now to the sensors  1604  of the waveguide system  1602 , the sensors  1604  can comprise one or more of a temperature sensor  1604   a , a disturbance detection sensor  1604   b , a loss of energy sensor  1604   c , a noise sensor  1604   d , a vibration sensor  1604   e , an environmental (e.g., weather) sensor  1604   f , and/or an image sensor  1604   g . The temperature sensor  1604   a  can be used to measure ambient temperature, a temperature of the transmission device  101  or  102 , a temperature of the power line  1610 , temperature differentials (e.g., compared to a setpoint or baseline, between transmission device  101  or  102  and  1610 , etc.), or any combination thereof. In one embodiment, temperature metrics can be collected and reported periodically to a network management system  1601  by way of the base station  1614 . 
     The disturbance detection sensor  1604   b  can perform measurements on the power line  1610  to detect disturbances such as signal reflections, which may indicate a presence of a downstream disturbance that may impede the propagation of electromagnetic waves on the power line  1610 . A signal reflection can represent a distortion resulting from, for example, an electromagnetic wave transmitted on the power line  1610  by the transmission device  101  or  102  that reflects in whole or in part back to the transmission device  101  or  102  from a disturbance in the power line  1610  located downstream from the transmission device  101  or  102 . 
     Signal reflections can be caused by obstructions on the power line  1610 . For example, a tree limb may cause electromagnetic wave reflections when the tree limb is lying on the power line  1610 , or is in close proximity to the power line  1610  which may cause a corona discharge. Other obstructions that can cause electromagnetic wave reflections can include without limitation an object that has been entangled on the power line  1610  (e.g., clothing, a shoe wrapped around a power line  1610  with a shoe string, etc.), a corroded build-up on the power line  1610  or an ice build-up. Power grid components may also impede or obstruct with the propagation of electromagnetic waves on the surface of power lines  1610 . Illustrations of power grid components that may cause signal reflections include without limitation a transformer and a joint for connecting spliced power lines. A sharp angle on the power line  1610  may also cause electromagnetic wave reflections. 
     The disturbance detection sensor  1604   b  can comprise a circuit to compare magnitudes of electromagnetic wave reflections to magnitudes of original electromagnetic waves transmitted by the transmission device  101  or  102  to determine how much a downstream disturbance in the power line  1610  attenuates transmissions. The disturbance detection sensor  1604   b  can further comprise a spectral analyzer circuit for performing spectral analysis on the reflected waves. The spectral data generated by the spectral analyzer circuit can be compared with spectral profiles via pattern recognition, an expert system, curve fitting, matched filtering or other artificial intelligence, classification or comparison technique to identify a type of disturbance based on, for example, the spectral profile that most closely matches the spectral data. The spectral profiles can be stored in a memory of the disturbance detection sensor  1604   b  or may be remotely accessible by the disturbance detection sensor  1604   b . The profiles can comprise spectral data that models different disturbances that may be encountered on power lines  1610  to enable the disturbance detection sensor  1604   b  to identify disturbances locally. An identification of the disturbance if known can be reported to the network management system  1601  by way of the base station  1614 . The disturbance detection sensor  1604   b  can also utilize the transmission device  101  or  102  to transmit electromagnetic waves as test signals to determine a roundtrip time for an electromagnetic wave reflection. The round trip time measured by the disturbance detection sensor  1604   b  can be used to calculate a distance traveled by the electromagnetic wave up to a point where the reflection takes place, which enables the disturbance detection sensor  1604   b  to calculate a distance from the transmission device  101  or  102  to the downstream disturbance on the power line  1610 . 
     The distance calculated can be reported to the network management system  1601  by way of the base station  1614 . In one embodiment, the location of the waveguide system  1602  on the power line  1610  may be known to the network management system  1601 , which the network management system  1601  can use to determine a location of the disturbance on the power line  1610  based on a known topology of the power grid. In another embodiment, the waveguide system  1602  can provide its location to the network management system  1601  to assist in the determination of the location of the disturbance on the power line  1610 . The location of the waveguide system  1602  can be obtained by the waveguide system  1602  from a pre-programmed location of the waveguide system  1602  stored in a memory of the waveguide system  1602 , or the waveguide system  1602  can determine its location using a GPS receiver (not shown) included in the waveguide system  1602 . 
     The power management system  1605  provides energy to the aforementioned components of the waveguide system  1602 . The power management system  1605  can receive energy from solar cells, or from a transformer (not shown) coupled to the power line  1610 , or by inductive coupling to the power line  1610  or another nearby power line. The power management system  1605  can also include a backup battery and/or a super capacitor or other capacitor circuit for providing the waveguide system  1602  with temporary power. The loss of energy sensor  1604   c  can be used to detect when the waveguide system  1602  has a loss of power condition and/or the occurrence of some other malfunction. For example, the loss of energy sensor  1604   c  can detect when there is a loss of power due to defective solar cells, an obstruction on the solar cells that causes them to malfunction, loss of power on the power line  1610 , and/or when the backup power system malfunctions due to expiration of a backup battery, or a detectable defect in a super capacitor. When a malfunction and/or loss of power occurs, the loss of energy sensor  1604   c  can notify the network management system  1601  by way of the base station  1614 . 
     The noise sensor  1604   d  can be used to measure noise on the power line  1610  that may adversely affect transmission of electromagnetic waves on the power line  1610 . The noise sensor  1604   d  can sense unexpected electromagnetic interference, noise bursts, or other sources of disturbances that may interrupt reception of modulated electromagnetic waves on a surface of a power line  1610 . A noise burst can be caused by, for example, a corona discharge, or other source of noise. The noise sensor  1604   d  can compare the measured noise to a noise profile obtained by the waveguide system  1602  from an internal database of noise profiles or from a remotely located database that stores noise profiles via pattern recognition, an expert system, curve fitting, matched filtering or other artificial intelligence, classification or comparison technique. From the comparison, the noise sensor  1604   d  may identify a noise source (e.g., corona discharge or otherwise) based on, for example, the noise profile that provides the closest match to the measured noise. The noise sensor  1604   d  can also detect how noise affects transmissions by measuring transmission metrics such as bit error rate, packet loss rate, jitter, packet retransmission requests, etc. The noise sensor  1604   d  can report to the network management system  1601  by way of the base station  1614  the identity of noise sources, their time of occurrence, and transmission metrics, among other things. 
     The vibration sensor  1604   e  can include accelerometers and/or gyroscopes to detect 2D or 3D vibrations on the power line  1610 . The vibrations can be compared to vibration profiles that can be stored locally in the waveguide system  1602 , or obtained by the waveguide system  1602  from a remote database via pattern recognition, an expert system, curve fitting, matched filtering or other artificial intelligence, classification or comparison technique. Vibration profiles can be used, for example, to distinguish fallen trees from wind gusts based on, for example, the vibration profile that provides the closest match to the measured vibrations. The results of this analysis can be reported by the vibration sensor  1604   e  to the network management system  1601  by way of the base station  1614 . 
     The environmental sensor  1604   f  can include a barometer for measuring atmospheric pressure, ambient temperature (which can be provided by the temperature sensor  1604   a ), wind speed, humidity, wind direction, and rainfall, among other things. The environmental sensor  1604   f  can collect raw information and process this information by comparing it to environmental profiles that can be obtained from a memory of the waveguide system  1602  or a remote database to predict weather conditions before they arise via pattern recognition, an expert system, knowledge-based system or other artificial intelligence, classification or other weather modeling and prediction technique. The environmental sensor  1604   f  can report raw data as well as its analysis to the network management system  1601 . 
     The image sensor  1604   g  can be a digital camera (e.g., a charged coupled device or CCD imager, infrared camera, etc.) for capturing images in a vicinity of the waveguide system  1602 . The image sensor  1604   g  can include an electromechanical mechanism to control movement (e.g., actual position or focal points/zooms) of the camera for inspecting the power line  1610  from multiple perspectives (e.g., top surface, bottom surface, left surface, right surface and so on). Alternatively, the image sensor  1604   g  can be designed such that no electromechanical mechanism is needed in order to obtain the multiple perspectives. The collection and retrieval of imaging data generated by the image sensor  1604   g  can be controlled by the network management system  1601 , or can be autonomously collected and reported by the image sensor  1604   g  to the network management system  1601 . 
     Other sensors that may be suitable for collecting telemetry information associated with the waveguide system  1602  and/or the power lines  1610  for purposes of detecting, predicting and/or mitigating disturbances that can impede the propagation of electromagnetic wave transmissions on power lines  1610  (or any other form of a transmission medium of electromagnetic waves) may be utilized by the waveguide system  1602 . 
     Referring now to  FIG. 16B , block diagram  1650  illustrates an example, non-limiting embodiment of a system for managing a power grid  1653  and a communication system  1655  embedded therein or associated therewith in accordance with various aspects described herein. The communication system  1655  comprises a plurality of waveguide systems  1602  coupled to power lines  1610  of the power grid  1653 . At least a portion of the waveguide systems  1602  used in the communication system  1655  can be in direct communication with a base station  1614  and/or the network management system  1601 . Waveguide systems  1602  not directly connected to a base station  1614  or the network management system  1601  can engage in communication sessions with either a base station  1614  or the network management system  1601  by way of other downstream waveguide systems  1602  connected to a base station  1614  or the network management system  1601 . 
     The network management system  1601  can be communicatively coupled to equipment of a utility company  1652  and equipment of a communications service provider  1654  for providing each entity, status information associated with the power grid  1653  and the communication system  1655 , respectively. The network management system  1601 , the equipment of the utility company  1652 , and the communications service provider  1654  can access communication devices utilized by utility company personnel  1656  and/or communication devices utilized by communications service provider personnel  1658  for purposes of providing status information and/or for directing such personnel in the management of the power grid  1653  and/or communication system  1655 . 
       FIG. 17A  illustrates a flow diagram of an example, non-limiting embodiment of a method  1700  for detecting and mitigating disturbances occurring in a communication network of the systems of  FIGS. 16A &amp; 16B . Method  1700  can begin with step  1702  where a waveguide system  1602  transmits and receives messages embedded in, or forming part of, modulated electromagnetic waves or another type of electromagnetic waves traveling along a surface of a power line  1610 . The messages can be voice messages, streaming video, and/or other data/information exchanged between communication devices communicatively coupled to the communication system  1655 . At step  1704  the sensors  1604  of the waveguide system  1602  can collect sensing data. In an embodiment, the sensing data can be collected in step  1704  prior to, during, or after the transmission and/or receipt of messages in step  1702 . At step  1706  the waveguide system  1602  (or the sensors  1604  themselves) can determine from the sensing data an actual or predicted occurrence of a disturbance in the communication system  1655  that can affect communications originating from (e.g., transmitted by) or received by the waveguide system  1602 . The waveguide system  1602  (or the sensors  1604 ) can process temperature data, signal reflection data, loss of energy data, noise data, vibration data, environmental data, or any combination thereof to make this determination. The waveguide system  1602  (or the sensors  1604 ) may also detect, identify, estimate, or predict the source of the disturbance and/or its location in the communication system  1655 . If a disturbance is neither detected/identified nor predicted/estimated at step  1708 , the waveguide system  1602  can proceed to step  1702  where it continues to transmit and receive messages embedded in, or forming part of, modulated electromagnetic waves traveling along a surface of the power line  1610 . 
     If at step  1708  a disturbance is detected/identified or predicted/estimated to occur, the waveguide system  1602  proceeds to step  1710  to determine if the disturbance adversely affects (or alternatively, is likely to adversely affect or the extent to which it may adversely affect) transmission or reception of messages in the communication system  1655 . In one embodiment, a duration threshold and a frequency of occurrence threshold can be used at step  1710  to determine when a disturbance adversely affects communications in the communication system  1655 . For illustration purposes only, assume a duration threshold is set to 500 ms, while a frequency of occurrence threshold is set to 5 disturbances occurring in an observation period of 10 sec. Thus, a disturbance having a duration greater than 500 ms will trigger the duration threshold. Additionally, any disturbance occurring more than 5 times in a 10 sec time interval will trigger the frequency of occurrence threshold. 
     In one embodiment, a disturbance may be considered to adversely affect signal integrity in the communication systems  1655  when the duration threshold alone is exceeded. In another embodiment, a disturbance may be considered as adversely affecting signal integrity in the communication systems  1655  when both the duration threshold and the frequency of occurrence threshold are exceeded. The latter embodiment is thus more conservative than the former embodiment for classifying disturbances that adversely affect signal integrity in the communication system  1655 . It will be appreciated that many other algorithms and associated parameters and thresholds can be utilized for step  1710  in accordance with example embodiments. 
     Referring back to method  1700 , if at step  1710  the disturbance detected at step  1708  does not meet the condition for adversely affected communications (e.g., neither exceeds the duration threshold nor the frequency of occurrence threshold), the waveguide system  1602  may proceed to step  1702  and continue processing messages. For instance, if the disturbance detected in step  1708  has a duration of 1 msec with a single occurrence in a 10 sec time period, then neither threshold will be exceeded. Consequently, such a disturbance may be considered as having a nominal effect on signal integrity in the communication system  1655  and thus would not be flagged as a disturbance requiring mitigation. Although not flagged, the occurrence of the disturbance, its time of occurrence, its frequency of occurrence, spectral data, and/or other useful information, may be reported to the network management system  1601  as telemetry data for monitoring purposes. 
     Referring back to step  1710 , if on the other hand the disturbance satisfies the condition for adversely affected communications (e.g., exceeds either or both thresholds), the waveguide system  1602  can proceed to step  1712  and report the incident to the network management system  1601 . The report can include raw sensing data collected by the sensors  1604 , a description of the disturbance if known by the waveguide system  1602 , a time of occurrence of the disturbance, a frequency of occurrence of the disturbance, a location associated with the disturbance, parameters readings such as bit error rate, packet loss rate, retransmission requests, jitter, latency and so on. If the disturbance is based on a prediction by one or more sensors of the waveguide system  1602 , the report can include a type of disturbance expected, and if predictable, an expected time occurrence of the disturbance, and an expected frequency of occurrence of the predicted disturbance when the prediction is based on historical sensing data collected by the sensors  1604  of the waveguide system  1602 . 
     At step  1714 , the network management system  1601  can determine a mitigation, circumvention, or correction technique, which may include directing the waveguide system  1602  to reroute traffic to circumvent the disturbance if the location of the disturbance can be determined. In one embodiment, the waveguide coupling device  1402  detecting the disturbance may direct a repeater such as the one shown in  FIGS. 13-14  to connect the waveguide system  1602  from a primary power line affected by the disturbance to a secondary power line to enable the waveguide system  1602  to reroute traffic to a different transmission medium and avoid the disturbance. In an embodiment where the waveguide system  1602  is configured as a repeater the waveguide system  1602  can itself perform the rerouting of traffic from the primary power line to the secondary power line. It is further noted that for bidirectional communications (e.g., full or half-duplex communications), the repeater can be configured to reroute traffic from the secondary power line back to the primary power line for processing by the waveguide system  1602 . 
     In another embodiment, the waveguide system  1602  can redirect traffic by instructing a first repeater situated upstream of the disturbance and a second repeater situated downstream of the disturbance to redirect traffic from a primary power line temporarily to a secondary power line and back to the primary power line in a manner that avoids the disturbance. It is further noted that for bidirectional communications (e.g., full or half-duplex communications), repeaters can be configured to reroute traffic from the secondary power line back to the primary power line. 
     To avoid interrupting existing communication sessions occurring on a secondary power line, the network management system  1601  may direct the waveguide system  1602  to instruct repeater(s) to utilize unused time slot(s) and/or frequency band(s) of the secondary power line for redirecting data and/or voice traffic away from the primary power line to circumvent the disturbance. 
     At step  1716 , while traffic is being rerouted to avoid the disturbance, the network management system  1601  can notify equipment of the utility company  1652  and/or equipment of the communications service provider  1654 , which in turn may notify personnel of the utility company  1656  and/or personnel of the communications service provider  1658  of the detected disturbance and its location if known. Field personnel from either party can attend to resolving the disturbance at a determined location of the disturbance. Once the disturbance is removed or otherwise mitigated by personnel of the utility company and/or personnel of the communications service provider, such personnel can notify their respective companies and/or the network management system  1601  utilizing field equipment (e.g., a laptop computer, smartphone, etc.) communicatively coupled to network management system  1601 , and/or equipment of the utility company and/or the communications service provider. The notification can include a description of how the disturbance was mitigated and any changes to the power lines  1610  that may change a topology of the communication system  1655 . 
     Once the disturbance has been resolved (as determined in decision  1718 ), the network management system  1601  can direct the waveguide system  1602  at step  1720  to restore the previous routing configuration used by the waveguide system  1602  or route traffic according to a new routing configuration if the restoration strategy used to mitigate the disturbance resulted in a new network topology of the communication system  1655 . In another embodiment, the waveguide system  1602  can be configured to monitor mitigation of the disturbance by transmitting test signals on the power line  1610  to determine when the disturbance has been removed. Once the waveguide system  1602  detects an absence of the disturbance it can autonomously restore its routing configuration without assistance by the network management system  1601  if it determines the network topology of the communication system  1655  has not changed, or it can utilize a new routing configuration that adapts to a detected new network topology. 
       FIG. 17B  illustrates a flow diagram of an example, non-limiting embodiment of a method  1750  for detecting and mitigating disturbances occurring in a communication network of the system of  FIGS. 16A and 16B . In one embodiment, method  1750  can begin with step  1752  where a network management system  1601  receives from equipment of the utility company  1652  or equipment of the communications service provider  1654  maintenance information associated with a maintenance schedule. The network management system  1601  can at step  1754  identify from the maintenance information, maintenance activities to be performed during the maintenance schedule. From these activities, the network management system  1601  can detect a disturbance resulting from the maintenance (e.g., scheduled replacement of a power line  1610 , scheduled replacement of a waveguide system  1602  on the power line  1610 , scheduled reconfiguration of power lines  1610  in the power grid  1653 , etc.). 
     In another embodiment, the network management system  1601  can receive at step  1755  telemetry information from one or more waveguide systems  1602 . The telemetry information can include among other things an identity of each waveguide system  1602  submitting the telemetry information, measurements taken by sensors  1604  of each waveguide system  1602 , information relating to predicted, estimated, or actual disturbances detected by the sensors  1604  of each waveguide system  1602 , location information associated with each waveguide system  1602 , an estimated location of a detected disturbance, an identification of the disturbance, and so on. The network management system  1601  can determine from the telemetry information a type of disturbance that may be adverse to operations of the waveguide, transmission of the electromagnetic waves along the wire surface, or both. The network management system  1601  can also use telemetry information from multiple waveguide systems  1602  to isolate and identify the disturbance. Additionally, the network management system  1601  can request telemetry information from waveguide systems  1602  in a vicinity of an affected waveguide system  1602  to triangulate a location of the disturbance and/or validate an identification of the disturbance by receiving similar telemetry information from other waveguide systems  1602 . 
     In yet another embodiment, the network management system  1601  can receive at step  1756  an unscheduled activity report from maintenance field personnel. Unscheduled maintenance may occur as result of field calls that are unplanned or as a result of unexpected field issues discovered during field calls or scheduled maintenance activities. The activity report can identify changes to a topology configuration of the power grid  1653  resulting from field personnel addressing discovered issues in the communication system  1655  and/or power grid  1653 , changes to one or more waveguide systems  1602  (such as replacement or repair thereof), mitigation of disturbances performed if any, and so on. 
     At step  1758 , the network management system  1601  can determine from reports received according to steps  1752  through  1756  if a disturbance will occur based on a maintenance schedule, or if a disturbance has occurred or is predicted to occur based on telemetry data, or if a disturbance has occurred due to an unplanned maintenance identified in a field activity report. From any of these reports, the network management system  1601  can determine whether a detected or predicted disturbance requires rerouting of traffic by the affected waveguide systems  1602  or other waveguide systems  1602  of the communication system  1655 . 
     When a disturbance is detected or predicted at step  1758 , the network management system  1601  can proceed to step  1760  where it can direct one or more waveguide systems  1602  to reroute traffic to circumvent the disturbance. When the disturbance is permanent due to a permanent topology change of the power grid  1653 , the network management system  1601  can proceed to step  1770  and skip steps  1762 ,  1764 ,  1766 , and  1772 . At step  1770 , the network management system  1601  can direct one or more waveguide systems  1602  to use a new routing configuration that adapts to the new topology. However, when the disturbance has been detected from telemetry information supplied by one or more waveguide systems  1602 , the network management system  1601  can notify maintenance personnel of the utility company  1656  or the communications service provider  1658  of a location of the disturbance, a type of disturbance if known, and related information that may be helpful to such personnel to mitigate the disturbance. When a disturbance is expected due to maintenance activities, the network management system  1601  can direct one or more waveguide systems  1602  to reconfigure traffic routes at a given schedule (consistent with the maintenance schedule) to avoid disturbances caused by the maintenance activities during the maintenance schedule. 
     Returning back to step  1760  and upon its completion, the process can continue with step  1762 . At step  1762 , the network management system  1601  can monitor when the disturbance(s) have been mitigated by field personnel. Mitigation of a disturbance can be detected at step  1762  by analyzing field reports submitted to the network management system  1601  by field personnel over a communications network (e.g., cellular communication system) utilizing field equipment (e.g., a laptop computer or handheld computer/device). If field personnel have reported that a disturbance has been mitigated, the network management system  1601  can proceed to step  1764  to determine from the field report whether a topology change was required to mitigate the disturbance. A topology change can include rerouting a power line  1610 , reconfiguring a waveguide system  1602  to utilize a different power line  1610 , otherwise utilizing an alternative link to bypass the disturbance and so on. If a topology change has taken place, the network management system  1601  can direct at step  1770  one or more waveguide systems  1602  to use a new routing configuration that adapts to the new topology. 
     If, however, a topology change has not been reported by field personnel, the network management system  1601  can proceed to step  1766  where it can direct one or more waveguide systems  1602  to send test signals to test a routing configuration that had been used prior to the detected disturbance(s). Test signals can be sent to affected waveguide systems  1602  in a vicinity of the disturbance. The test signals can be used to determine if signal disturbances (e.g., electromagnetic wave reflections) are detected by any of the waveguide systems  1602 . If the test signals confirm that a prior routing configuration is no longer subject to previously detected disturbance(s), then the network management system  1601  can at step  1772  direct the affected waveguide systems  1602  to restore a previous routing configuration. If, however, test signals analyzed by one or more waveguide coupling device  1402  and reported to the network management system  1601  indicate that the disturbance(s) or new disturbance(s) are present, then the network management system  1601  will proceed to step  1768  and report this information to field personnel to further address field issues. The network management system  1601  can in this situation continue to monitor mitigation of the disturbance(s) at step  1762 . 
     In the aforementioned embodiments, the waveguide systems  1602  can be configured to be self-adapting to changes in the power grid  1653  and/or to mitigation of disturbances. That is, one or more affected waveguide systems  1602  can be configured to self-monitor mitigation of disturbances and reconfigure traffic routes without requiring instructions to be sent to them by the network management system  1601 . In this embodiment, the one or more waveguide systems  1602  that are self-configurable can inform the network management system  1601  of its routing choices so that the network management system  1601  can maintain a macro-level view of the communication topology of the communication system  1655 . 
     While for purposes of simplicity of explanation, the respective processes are shown and described as a series of blocks in  FIGS. 17A and 17B , respectively, it is to be understood and appreciated that the claimed subject matter is not limited by the order of the blocks, as some blocks may occur in different orders and/or concurrently with other blocks from what is depicted and described herein. Moreover, not all illustrated blocks may be required to implement the methods described herein. 
     Turning now to  FIG. 18A , a block diagram illustrating an example, non-limiting embodiment of a transmission medium  1800  for propagating guided electromagnetic waves is shown. In particular, a further example of transmission medium  125  presented in conjunction with  FIG. 1  is presented. In an embodiment, the transmission medium  1800  can comprise a first dielectric material  1802  and a second dielectric material  1804  disposed thereon. In an embodiment, the first dielectric material  1802  can comprise a dielectric core (referred to herein as dielectric core  1802 ) and the second dielectric material  1804  can comprise a cladding or shell such as a dielectric foam that surrounds in whole or in part the dielectric core (referred to herein as dielectric foam  1804 ). In an embodiment, the dielectric core  1802  and dielectric foam  1804  can be coaxially aligned to each other (although not necessary). In an embodiment, the combination of the dielectric core  1802  and the dielectric foam  1804  can be flexed or bent at least by 45 degrees without damaging the materials of the dielectric core  1802  and the dielectric foam  1804 . In an embodiment, an outer surface of the dielectric foam  1804  can be further surrounded in whole or in part by a third dielectric material  1806 , which can serve as an outer jacket (referred to herein as jacket  1806 ). The jacket  1806  can prevent exposure of the dielectric core  1802  and the dielectric foam  1804  to an environment that can adversely affect the propagation of electromagnetic waves (e.g., water, soil, etc.). 
     The dielectric core  1802  can comprise, for example, a high density polyethylene material, a high density polyurethane material, or other suitable dielectric material(s). The dielectric foam  1804  can comprise, for example, a cellular plastic material such an expanded polyethylene material, or other suitable dielectric material(s). The jacket  1806  can comprise, for example, a polyethylene material or equivalent. In an embodiment, the dielectric constant of the dielectric foam  1804  can be (or substantially) lower than the dielectric constant of the dielectric core  1802 . For example, the dielectric constant of the dielectric core  1802  can be approximately 2.3 while the dielectric constant of the dielectric foam  1804  can be approximately 1.15 (slightly higher than the dielectric constant of air). 
     The dielectric core  1802  can be used for receiving signals in the form of electromagnetic waves from a launcher or other coupling device described herein which can be configured to launch guided electromagnetic waves on the transmission medium  1800 . In one embodiment, the transmission  1800  can be coupled to a hollow waveguide  1808  structured as, for example, a circular waveguide  1809 , which can receive electromagnetic waves from a radiating device such as a stub antenna (not shown). The hollow waveguide  1808  can in turn induce guided electromagnetic waves in the dielectric core  1802 . In this configuration, the guided electromagnetic waves are guided by or bound to the dielectric core  1802  and propagate longitudinally along the dielectric core  1802 . By adjusting electronics of the launcher, an operating frequency of the electromagnetic waves can be chosen such that a field intensity profile  1810  of the guided electromagnetic waves extends nominally (or not at all) outside of the jacket  1806 . 
     By maintaining most (if not all) of the field strength of the guided electromagnetic waves within portions of the dielectric core  1802 , the dielectric foam  1804  and/or the jacket  1806 , the transmission medium  1800  can be used in hostile environments without adversely affecting the propagation of the electromagnetic waves propagating therein. For example, the transmission medium  1800  can be buried in soil with no (or nearly no) adverse effect to the guided electromagnetic waves propagating in the transmission medium  1800 . Similarly, the transmission medium  1800  can be exposed to water (e.g., rain or placed underwater) with no (or nearly no) adverse effect to the guided electromagnetic waves propagating in the transmission medium  1800 . In an embodiment, the propagation loss of guided electromagnetic waves in the foregoing embodiments can be 1 to 2 dB per meter or better at an operating frequency of 60 GHz. Depending on the operating frequency of the guided electromagnetic waves and/or the materials used for the transmission medium  1800  other propagation losses may be possible. Additionally, depending on the materials used to construct the transmission medium  1800 , the transmission medium  1800  can in some embodiments be flexed laterally with no (or nearly no) adverse effect to the guided electromagnetic waves propagating through the dielectric core  1802  and the dielectric foam  1804 . 
     Other configurations of the transmission medium  1800  are possible including, a transmission medium that comprises a conductive core with or without an insulation layer surrounding the conductive core in whole or in part that is, in turn, covered in whole or in part by a dielectric foam  1804  and jacket  1806 , which can be constructed from the materials previously described. 
     It should be noted that the hollow launcher  1808  used with the transmission medium  1800  can be replaced with other launchers, couplers or coupling devices described in the subject disclosure. Additionally, the propagation mode(s) of the electromagnetic waves for any of the foregoing embodiments can be fundamental mode(s), non-fundamental mode(s), or combinations thereof. 
       FIG. 18B  is a block diagram illustrating an example, non-limiting embodiment of bundled transmission media  1836  in accordance with various aspects described herein. The bundled transmission media  1836  can comprise a plurality of cables  1838  held in place by a flexible sleeve  1839 . The plurality of cables  1838  can comprise multiple instances of cable  1800  of  FIG. 18A . The sleeve  1839  can comprise a dielectric material that prevents soil, water or other external materials from making contact with the plurality of cables  1838 . In an embodiment, a plurality of launchers, each utilizing a transceiver similar to the one depicted in  FIG. 10  or other coupling devices described herein, can be adapted to selectively induce a guided electromagnetic wave in each cable, each guided electromagnetic wave conveys different data (e.g., voice, video, messaging, content, etc.). In an embodiment, by adjusting operational parameters of each launcher or other coupling device, the electric field intensity profile of each guided electromagnetic wave can be fully or substantially confined within layers of a corresponding cable  1838  to reduce cross-talk between cables  1838 . 
     In situations where the electric field intensity profile of each guided electromagnetic wave is not fully or substantially confined within a corresponding cable  1838 , cross-talk of electromagnetic signals can occur between cables  1838 . Several mitigation options can be used to reduce cross-talk between the cables  1838  of  FIG. 18B . In an embodiment, an absorption material  1840  that can absorb electromagnetic fields, such as carbon, can be applied to the cables  1838  as shown in  FIG. 18B  to polarize each guided electromagnetic wave at various polarization states to reduce cross-talk between cables  1838 . In another embodiment (not shown), carbon beads can be added to gaps between the cables  1838  to reduce cross-talk. 
     In yet another embodiment (not shown), a diameter of cable  1838  can be configured differently to vary a speed of propagation of guided electromagnetic waves between the cables  1838  in order to reduce cross-talk between cables  1838 . In an embodiment (not shown), a shape of each cable  1838  can be made asymmetric (e.g., elliptical) to direct the guided electromagnetic fields of each cable  1838  away from each other to reduce cross-talk. In an embodiment (not shown), a filler material such as dielectric foam can be added between cables  1838  to sufficiently separate the cables  1838  to reduce cross-talk therebetween. In an embodiment (not shown), longitudinal carbon strips or swirls can be applied to on an outer surface of the jacket  1806  of each cable  1838  to reduce radiation of guided electromagnetic waves outside of the jacket  1806  and thereby reduce cross-talk between cables  1838 . In yet another embodiment, each launcher can be configured to launch a guided electromagnetic wave having a different frequency, modulation, wave propagation mode, such as an orthogonal frequency, modulation or mode, to reduce cross-talk between the cables  1838 . 
     In yet another embodiment (not shown), pairs of cables  1838  can be twisted in a helix to reduce cross-talk between the pairs and other cables  1838  in a vicinity of the pairs. In some embodiments, certain cables  1838  can be twisted while other cables  1838  are not twisted to reduce cross-talk between the cables  1838 . Additionally, each twisted pair cable  1838  can have different pitches (i.e., different twist rates, such as twists per meter) to further reduce cross-talk between the pairs and other cables  1838  in a vicinity of the pairs. In another embodiment (not shown), launchers or other coupling devices can be configured to induce guided electromagnetic waves in the cables  1838  having electromagnetic fields that extend beyond the jacket  1806  into gaps between the cables to reduce cross-talk between the cables  1838 . It is submitted that any one of the foregoing embodiments for mitigating cross-talk between cables  1838  can be combined to further reduce cross-talk therebetween. 
     Turning now to  FIG. 18C , a block diagram illustrating an example, non-limiting embodiment of exposed tapered stubs from the bundled transmission media  1836  for use as antennas  1855  is shown. Each antenna  1855  can serve as a directional antenna for radiating wireless signals directed to wireless communication devices or for inducing electromagnetic wave propagation on a surface of a transmission medium (e.g., a power line). In an embodiment, the wireless signals radiated by the antennas  1855  can be beam steered by adapting the phase and/or other characteristics of the wireless signals generated by each antenna  1855 . In an embodiment, the antennas  1855  can individually be placed in a pie-pan antenna assembly for directing wireless signals in various directions. 
     It is further noted that the terms “core”, “cladding”, “shell”, and “foam” as utilized in the subject disclosure can comprise any types of materials (or combinations of materials) that enable electromagnetic waves to remain bound to the core while propagating longitudinally along the core. For example, a strip of dielectric foam  1804 ″ described earlier can be replaced with a strip of an ordinary dielectric material (e.g., polyethylene) for wrapping around the dielectric core  1802  (referred to herein for illustration purposes only as a “wrap”). In this configuration an average density of the wrap can be small as a result of air space between sections of the wrap. Consequently, an effective dielectric constant of the wrap can be less than the dielectric constant of the dielectric core  1802 , thereby enabling guided electromagnetic waves to remain bound to the core. Accordingly, any of the embodiments of the subject disclosure relating to materials used for core(s) and wrappings about the core(s) can be structurally adapted and/or modified with other dielectric materials that achieve the result of maintaining electromagnetic waves bound to the core(s) while they propagate along the core(s). Additionally, a core in whole or in part as described in any of the embodiments of the subject disclosure can comprise an opaque material (e.g., polyethylene) that is resistant to propagation of electromagnetic waves having an optical operating frequency. 
     Accordingly, electromagnetic waves guided and bound to the core will have a non-optical frequency range (e.g., less than the lowest frequency of visible light). 
       FIGS. 18D, 18E, 18F, 18G, 18H, and 18I and 18J  are block diagrams illustrating example, non-limiting embodiments of a waveguide device for transmitting or receiving electromagnetic waves in accordance with various aspects described herein. In an embodiment,  FIG. 18D  illustrates a front view of a waveguide device  1865  having a plurality of slots  1863  (e.g., openings or apertures) for emitting electromagnetic waves having radiated electric fields (e-fields)  1861 . In an embodiment, the radiated e-fields  1861  of pairs of symmetrically positioned slots  1863  (e.g., north and south slots of the waveguide  1865 ) can be directed away from each other (i.e., polar opposite radial orientations about the cable  1862 ). While the slots  1863  are shown as having a rectangular shape, other shapes such as other polygons, sector and arc shapes, ellipsoid shapes and other shapes are likewise possible. For illustration purposes only, the term north will refer to a relative azimuthal direction/orientation as shown in the figures. All references in the subject disclosure to other directions/orientations (e.g., south, east, west, northwest, and so forth) will be relative to northern illustration. In an embodiment, to achieve e-fields with opposing orientations at the north and south slots  1863 , for example, the north and south slots  1863  can be arranged to have a circumferential distance between each other that is approximately one wavelength of electromagnetic waves signals supplied to these slots. The waveguide  1865  can have a cylindrical cavity in a center of the waveguide  1865  to enable placement of a cable  1862 . In one embodiment, the cable  1862  can comprise an insulated conductor. In another embodiment, the cable  1862  can comprise an uninsulated conductor. In yet other embodiments, the cable  1862  can comprise any of the embodiments of a transmission core  1852  of cable  1850  previously described. 
     In one embodiment, the cable  1862  can slide into the cylindrical cavity of the waveguide  1865 . In another embodiment, the waveguide  1865  can utilize an assembly mechanism (not shown). The assembly mechanism (e.g., a hinge or other suitable mechanism that provides a way to open the waveguide  1865  at one or more locations) can be used to enable placement of the waveguide  1865  on an outer surface of the cable  1862  or otherwise to assemble separate pieces together to form the waveguide  1865  as shown. According to these and other suitable embodiments, the waveguide  1865  can be configured to wrap around the cable  1862  like a collar. 
       FIG. 18E  illustrates a side view of an embodiment of the waveguide  1865 . The waveguide  1865  can be adapted to have a hollow rectangular waveguide portion  1867  that receives electromagnetic waves  1866  generated by a transmitter circuit as previously described in the subject disclosure (e.g., see  FIGS. 1 and 10 ). The electromagnetic waves  1866  can be distributed by the hollow rectangular waveguide portion  1867  into in a hollow collar  1869  of the waveguide  1865 . The rectangular waveguide portion  1867  and the hollow collar  1869  can be constructed of materials suitable for maintaining the electromagnetic waves within the hollow chambers of these assemblies (e.g., carbon fiber materials). It should be noted that while the waveguide portion  1867  is shown and described in a hollow rectangular configuration, other shapes and/or other non-hollow configurations can be employed. In particular, the waveguide portion  1867  can have a square or other polygonal cross section, an arc or sector cross section that is truncated to conform to the outer surface of the cable  1862 , a circular or ellipsoid cross section or cross sectional shape. In addition, the waveguide portion  1867  can be configured as, or otherwise include, a solid dielectric material. 
     As previously described, the hollow collar  1869  can be configured to emit electromagnetic waves from each slot  1863  with opposite e-fields  1861  at pairs of symmetrically positioned slots  1863  and  1863 ′. In an embodiment, the electromagnetic waves emitted by the combination of slots  1863  and  1863 ′ can in turn induce electromagnetic waves  1868  on that are bound to the cable  1862  for propagation according to a fundamental wave mode without other wave modes present—such as non-fundamental wave modes. In this configuration, the electromagnetic waves  1868  can propagate longitudinally along the cable  1862  to other downstream waveguide systems coupled to the cable  1862 . 
     It should be noted that since the hollow rectangular waveguide portion  1867  of  FIG. 18E  is closer to slot  1863  (at the northern position of the waveguide  1865 ), slot  1863  can emit electromagnetic waves having a stronger magnitude than electromagnetic waves emitted by slot  1863 ′ (at the southern position). To reduce magnitude differences between these slots, slot  1863 ′ can be made larger than slot  1863 . The technique of utilizing different slot sizes to balance signal magnitudes between slots can be applied to any of the embodiments of the subject disclosure relating to  FIGS. 18D, 18E, 18G, and 18I —some of which are described below. 
     In another embodiment,  FIG. 18F  depicts a waveguide  1865 ′ that can be configured to utilize circuitry such as monolithic microwave integrated circuits (MMICs)  1870  each coupled to a signal input  1872  (e.g., coaxial cable that provides a communication signal). The signal input  1872  can be generated by a transmitter circuit as previously described in the subject disclosure (e.g., see reference  101 ,  1000  of  FIGS. 1 and 10 ) adapted to provide electrical signals to the MMICs  1870 . Each MMIC  1870  can be configured to receive signal  1872  which the MMIC  1870  can modulate and transmit with a radiating element (e.g., an antenna) to emit electromagnetic waves having radiated e-fields  1861 . In one embodiment, the MMICs  1870  can be configured to receive the same signal  1872 , but transmit electromagnetic waves having e-fields  1861  of opposing orientation. This can be accomplished by configuring one of the MMICs  1870  to transmit electromagnetic waves that are 180 degrees out of phase with the electromagnetic waves transmitted by the other MMIC  1870 . In an embodiment, the combination of the electromagnetic waves emitted by the MMICs  1870  can together induce electromagnetic waves  1868  that are bound to the cable  1862  for propagation according to a fundamental wave mode without other wave modes present—such as non-fundamental wave modes. In this configuration, the electromagnetic waves  1868  can propagate longitudinally along the cable  1862  to other downstream waveguide systems coupled to the cable  1862 . 
     A tapered horn  1880  can be added to the embodiments of  FIGS. 18E and 18F  to assist in the inducement of the electromagnetic waves  1868  on cable  1862  as depicted in  FIGS. 18G and 18H . In an embodiment where the cable  1862  is an uninsulated conductor, the electromagnetic waves induced on the cable  1862  can have a large radial dimension (e.g., 1 meter). To enable use of a smaller tapered horn  1880 , an insulation layer  1879  can be applied on a portion of the cable  1862  at or near the cavity as depicted with hash lines in  FIGS. 18G and 18H . The insulation layer  1879  can have a tapered end facing away from the waveguide  1865 . The added insulation enables the electromagnetic waves  1868  initially launched by the waveguide  1865  (or  1865 ′) to be tightly bound to the insulation, which in turn reduces the radial dimension of the electromagnetic fields  1868  (e.g., centimeters). As the electromagnetic waves  1868  propagate away from the waveguide  1865  ( 1865 ′) and reach the tapered end of the insulation layer  1879 , the radial dimension of the electromagnetic waves  1868  begin to increase eventually achieving the radial dimension they would have had had the electromagnetic waves  1868  been induced on the uninsulated conductor without an insulation layer. In the illustration of  FIGS. 18G and 18H  the tapered end begins at an end of the tapered horn  1880 . In other embodiments, the tapered end of the insulation layer  1879  can begin before or after the end of the tapered horn  1880 . The tapered horn can be metallic or constructed of other conductive material or constructed of a plastic or other non-conductive material that is coated or clad with a dielectric layer or doped with a conductive material to provide reflective properties similar to a metallic horn. 
     In an embodiment, cable  1862  can comprise any of the embodiments of cable  1850  described earlier. In this embodiment, waveguides  1865  and  1865 ′ can be coupled to a transmission core  1852  of cable  1850  as depicted in  FIGS. 18I and 18J . The waveguides  1865  and  1865 ′ can induce, as previously described, electromagnetic waves  1868  on the transmission core  1852  for propagation entirely or partially within inner layers of cable  1850 . 
     It is noted that for the foregoing embodiments of  FIGS. 18G, 18H, 18I and 18J , electromagnetic waves  1868  can be bidirectional. For example, electromagnetic waves  1868  of a different operating frequency can be received by slots  1863  or MMICs  1870  of the waveguides  1865  and  1865 ′, respectively. Once received, the electromagnetic waves can be converted by a receiver circuit (e.g., see reference  101 ,  1000  of  FIGS. 1 and 10 ) for generating a communication signal for processing. 
     Although not shown, it is further noted that the waveguides  1865  and  1865 ′ can be adapted so that the waveguides  1865  and  1865 ′ can direct electromagnetic waves  1868  upstream or downstream longitudinally. For example, a first tapered horn  1880  coupled to a first instance of a waveguide  1865  or  1865 ′ can be directed westerly on cable  1862 , while a second tapered horn  1880  coupled to a second instance of a waveguide  1865  or  1865 ′ can be directed easterly on cable  1862 . The first and second instances of the waveguides  1865  or  1865 ′ can be coupled so that in a repeater configuration, signals received by the first waveguide  1865  or  1865 ′ can be provided to the second waveguide  1865  or  1865 ′ for retransmission in an easterly direction on cable  1862 . The repeater configuration just described can also be applied from an easterly to westerly direction on cable  1862 . 
     In another embodiment, the waveguide  1865 ′ of  FIGS. 18G, 18H, 18I and 18J  can also be configured to generate electromagnetic waves having non-fundamental wave modes. This can be accomplished by adding more MMICs  1870  as depicted in  FIG. 18K . Each MMIC  1870  can be configured to receive the same signal input  1872 . However, MMICs  1870  can selectively be configured to emit electromagnetic waves having differing phases using controllable phase-shifting circuitry in each MMIC  1870 . For example, the northerly and southerly MMICs  1870  can be configured to emit electromagnetic waves having a 180 degree phase difference, thereby aligning the e-fields either in a northerly or southerly direction. Any combination of pairs of MMICs  1870  (e.g., westerly and easterly MMICs  1870 , northwesterly and southeasterly MMICs  1870 , northeasterly and southwesterly MMICs  1870 ) can be configured with opposing or aligned e-fields. Consequently, waveguide  1865 ′ can be configured to generate electromagnetic waves with one or more non-fundamental wave modes such as TMnm, HEnm or EHnm modes where n and m are non-negative integers and either n or m is non-zero, electromagnetic waves with one or more fundamental wave modes such as TM00, or any combinations thereof. 
     It is submitted that it is not necessary to select slots  1863  in pairs to generate electromagnetic waves having a non-fundamental wave mode. For example, electromagnetic waves having a non-fundamental wave mode can be generated by enabling a single slot from a plurality of slots and disabling all other slots. In particular, a single MMIC  1870  of the MMICs  1870  shown in  FIG. 18K  can be configured to generate electromagnetic waves having a non-fundamental wave mode while all other MMICs  1870  are not in use or disabled. Likewise, other wave modes and wave mode combinations can be induced by enabling other non-null proper subsets of waveguide slots  1863  or the MMICs  1870 . 
     It is further noted that in some embodiments, the waveguide systems  1865  and  1865 ′ may generate combinations of fundamental and non-fundamental wave modes where one wave mode is dominant over the other. For example, in one embodiment electromagnetic waves generated by the waveguide systems  1865  and  1865 ′ may have a weak signal component that has a non-fundamental wave mode, and a substantially strong signal component that has a fundamental wave mode. Accordingly, in this embodiment, the electromagnetic waves have a substantially fundamental wave mode. In another embodiment electromagnetic waves generated by the waveguide systems  1865  and  1865 ′ may have a weak signal component that has a fundamental wave mode, and a substantially strong signal component that has a non-fundamental wave mode. Accordingly, in this embodiment, the electromagnetic waves have a substantially non-fundamental wave mode. Further, a non-dominant wave mode may be generated that propagates only trivial distances along the length of the transmission medium. 
     It is also noted that the waveguide systems  1865  and  1865 ′ can be configured to generate instances of electromagnetic waves that have wave modes that can differ from a resulting wave mode or modes of the combined electromagnetic wave. It is further noted that each MMIC  1870  of the waveguide system  1865 ′ of  FIG. 18K  can be configured to generate an instance of electromagnetic waves having wave characteristics that differ from the wave characteristics of another instance of electromagnetic waves generated by another MMIC  1870 . One MMIC  1870 , for example, can generate an instance of an electromagnetic wave having a spatial orientation and a phase, frequency, magnitude, electric field orientation, and/or magnetic field orientation that differs from the spatial orientation and phase, frequency, magnitude, electric field orientation, and/or magnetic field orientation of a different instance of another electromagnetic wave generated by another MMIC  1870 . The waveguide system  1865 ′ can thus be configured to generate instances of electromagnetic waves having different wave and spatial characteristics, which when combined achieve resulting electromagnetic waves having one or more desirable wave modes. 
     From these illustrations, it is submitted that the waveguide systems  1865  and  1865 ′ can be adapted to generate electromagnetic waves with one or more selectable wave modes. In one embodiment, for example, the waveguide systems  1865  and  1865 ′ can be adapted to select one or more wave modes and generate electromagnetic waves having a single wave mode or multiple wave modes selected and produced from a process of combining instances of electromagnetic waves having one or more configurable wave and spatial characteristics. In an embodiment, for example, parametric information can be stored in a look-up table. Each entry in the look-up table can represent a selectable wave mode. A selectable wave mode can represent a single wave mode, or a combination of wave modes. The combination of wave modes can have one or dominant wave modes. The parametric information can provide configuration information for generating instances of electromagnetic waves for producing resultant electromagnetic waves that have the desired wave mode. 
     For example, once a wave mode or modes is selected, the parametric information obtained from the look-up table from the entry associated with the selected wave mode(s) can be used to identify which of one or more MMICs  1870  to utilize, and/or their corresponding configurations to achieve electromagnetic waves having the desired wave mode(s). The parametric information may identify the selection of the one or more MMICs  1870  based on the spatial orientations of the MMICs  1870 , which may be required for producing electromagnetic waves with the desired wave mode. The parametric information can also provide information to configure each of the one or more MMICs  1870  with a particular phase, frequency, magnitude, electric field orientation, and/or magnetic field orientation which may or may not be the same for each of the selected MMICs  1870 . A look-up table with selectable wave modes and corresponding parametric information can be adapted for configuring the slotted waveguide system  1865 . 
     In some embodiments, a guided electromagnetic wave can be considered to have a desired wave mode if the corresponding wave mode propagates non-trivial distances on a transmission medium and has a field strength that is substantially greater in magnitude (e.g., 20 dB higher in magnitude) than other wave modes that may or may not be desirable. Such a desired wave mode or modes can be referred to as dominant wave mode(s) with the other wave modes being referred to as non-dominant wave modes. In a similar fashion, a guided electromagnetic wave that is said to be substantially without the fundamental wave mode has either no fundamental wave mode or a non-dominant fundamental wave mode. A guided electromagnetic wave that is said to be substantially without a non-fundamental wave mode has either no non-fundamental wave mode(s) or only non-dominant non-fundamental wave mode(s). In some embodiments, a guided electromagnetic wave that is said to have only a single wave mode or a selected wave mode may have only one corresponding dominant wave mode. 
     Turning now to  FIGS. 19A and 19B , block diagrams illustrating example, non-limiting embodiments of a dielectric antenna and corresponding gain and field intensity plots in accordance with various aspects described herein are shown.  FIG. 19A  depicts a dielectric horn antenna  1901  having a conical structure. The dielectric horn antenna  1901  is coupled to one end  1902 ′ of a feedline  1902  having a feed point  1902 ″ at an opposite end of the feedline  1902 . The dielectric horn antenna  1901  and the feedline  1902  (as well as other embodiments of the dielectric antenna described below in the subject disclosure) can be constructed of dielectric materials such as a polyethylene material, a polyurethane material or other suitable dielectric material (e.g., a synthetic resin, other plastics, etc.). The dielectric horn antenna  1901  and the feedline  1902  (as well as other embodiments of the dielectric antenna described below in the subject disclosure) can be conductorless and/or be substantially or entirely devoid of any conductive materials. 
     For example, the external surfaces  1907  of the dielectric horn antenna  1901  and the feedline  1902  can be non-conductive or substantially non-conductive with at least 95% of the external surface area being non-conductive and the dielectric materials used to construct the dielectric horn antenna  1901  and the feedline  1902  can be such that they substantially do not contain impurities that may be conductive (e.g., such as less than 1 part per thousand) or result in imparting conductive properties. In other embodiments, however, a limited number of conductive components can be used such as a metallic connector component used for coupling to the feed point  1902 ″ of the feedline  1902  with one or more screws, rivets or other coupling elements used to bind components to one another, and/or one or more structural elements that do not significantly alter the radiation pattern of the dielectric antenna. 
     The feed point  1902 ″ can be adapted to couple to a core  1852  such as core  1802  previously described by way of illustration in  FIG. 18A . In one embodiment, the feed point  1902 ″ can be coupled to the core  1852  utilizing a joint (not shown in  FIG. 19A ). Other embodiments for coupling the feed point  1902 ″ to the core  1852  can be used. In an embodiment, the joint can be configured to cause the feed point  1902 ″ to touch an endpoint of the core  1852 . In another embodiment, the joint can create a gap between the feed point  1902 ″ and an end of the core  1852 . In yet another embodiment, the joint can cause the feed point  1902 ″ and the core  1852  to be coaxially aligned or partially misaligned. Notwithstanding any combination of the foregoing embodiments, electromagnetic waves can in whole or at least in part propagate between the junction of the feed point  1902 ″ and the core  1852 . 
     The cable  1850  can be coupled to the waveguide system  1865  or the waveguide system  1865 ′. For illustration purposes only, reference will be made to the waveguide system  1865 ′. It is understood, however, that the waveguide system  1865  or other waveguide systems can also be utilized in accordance with the discussions that follow. The waveguide system  1865 ′ can be configured to select a wave mode (e.g., non-fundamental wave mode, fundamental wave mode, a hybrid wave mode, or combinations thereof as described earlier) and transmit instances of electromagnetic waves having a non-optical operating frequency (e.g., 60 GHz). The electromagnetic waves can be directed to an interface of the cable  1850 . 
     The instances of electromagnetic waves generated by the waveguide system  1865 ′ can induce a combined electromagnetic wave having the selected wave mode that propagates from the core  1852  to the feed point  1902 ″. The combined electromagnetic wave can propagate partly inside the core  1852  and partly on an outer surface of the core  1852 . Once the combined electromagnetic wave has propagated through the junction between the core  1852  and the feed point  1902 ″, the combined electromagnetic wave can continue to propagate partly inside the feedline  1902  and partly on an outer surface of the feedline  1902 . In some embodiments, the portion of the combined electromagnetic wave that propagates on the outer surface of the core  1852  and the feedline  1902  is small. In these embodiments, the combined electromagnetic wave can be said to be guided by and tightly coupled to the core  1852  and the feedline  1902  while propagating longitudinally towards the dielectric antenna  1901 . 
     When the combined electromagnetic wave reaches a proximal portion of the dielectric antenna  1901  (at a junction  1902 ′ between the feedline  1902  and the dielectric antenna  1901 ), the combined electromagnetic wave enters the proximal portion of the dielectric antenna  1901  and propagates longitudinally along an axis of the dielectric antenna  1901  (shown as a hashed line). By the time the combined electromagnetic wave reaches the aperture  1903 , the combined electromagnetic wave has an intensity pattern similar to the one shown by the side view and front view depicted in  FIG. 19B . The electric field intensity pattern of  FIG. 19B  shows that the electric fields of the combined electromagnetic waves are strongest in a center region of the aperture  1903  and weaker in the outer regions. In an embodiment, where the wave mode of the electromagnetic waves propagating in the dielectric antenna  1901  is a hybrid wave mode (e.g., HE11), the leakage of the electromagnetic waves at the external surfaces  1907  is reduced or in some instances eliminated. It is further noted that while the dielectric antenna  1901  is constructed of a solid dielectric material having no physical opening, the front or operating face of the dielectric antenna  1901  from which free space wireless signals are radiated or received will be referred to as the aperture  1903  of the dielectric antenna  1901  even though in some prior art systems the term aperture may be used to describe an opening of an antenna that radiates or receives free space wireless signals. Methods for launching a hybrid wave mode on cable  1850  is discussed below. 
     In an embodiment, the far-field antenna gain pattern depicted in  FIG. 19B  can be widened by decreasing the operating frequency of the combined electromagnetic wave from a nominal frequency. Similarly, the gain pattern can be narrowed by increasing the operating frequency of the combined electromagnetic wave from the nominal frequency. Accordingly, a width of a beam of wireless signals emitted by the aperture  1903  can be controlled by configuring the waveguide system  1865 ′ to increase or decrease the operating frequency of the combined electromagnetic wave. 
     The dielectric antenna  1901  of  FIG. 19A  can also be used for receiving wireless signals, such as free space wireless signals transmitted by either a similar antenna or conventional antenna design. Wireless signals received by the dielectric antenna  1901  at the aperture  1903  induce electromagnetic waves in the dielectric antenna  1901  that propagate towards the feedline  1902 . The electromagnetic waves continue to propagate from the feedline  1902  to the junction between the feed point  1902 ″ and an endpoint of the core  1852 , and are thereby delivered to the waveguide system  1865 ′ coupled to the cable  1850 . In this configuration, the waveguide system  1865 ′ can perform bidirectional communications utilizing the dielectric antenna  1901 . It is further noted that in some embodiments the core  1852  of the cable  1850  (shown with dashed lines) can be configured to be collinear with the feed point  1902 ″ to avoid a bend shown in  FIG. 19A . In some embodiments, a collinear configuration can reduce an alteration in the propagation of the electromagnetic due to the bend in cable  1850 . 
     Turning now to  FIG. 19C , a block diagram is shown illustrating an example, non-limiting embodiment of a dielectric antenna  1901  coupled to or integrally constructed with a lens  1912  in accordance with various aspects described herein. In one embodiment, the lens  1912  can comprise a dielectric material having a first dielectric constant that is substantially similar or equal to a second dielectric constant of the dielectric antenna  1901 . In other embodiments, the lens  1912  can comprise a dielectric material having a first dielectric constant that differs from a second dielectric constant of the dielectric antenna  1901 . In either of these embodiments, the shape of the lens  1912  can be chosen or formed so as to equalize the delays of the various electromagnetic waves propagating at different points in the dielectric antenna  1901 . In one embodiment, the lens  1912  can be an integral part of the dielectric antenna  1901  as depicted in the top diagram of  FIG. 19C  and in particular, the lens and dielectric antenna  1901  can be molded, machined or otherwise formed from a single piece of dielectric material. Alternatively, the lens  1912  can be an assembly component of the dielectric antenna  1901  as depicted in the bottom diagram of  FIG. 19C , which can be attached by way of an adhesive material, brackets on the outer edges, or other suitable attachment techniques. The lens  1912  can have a convex structure as shown in  FIG. 19C  which is adapted to adjust a propagation of electromagnetic waves in the dielectric antenna  1901 . While a round lens and conical dielectric antenna configuration is shown, other shapes include pyramidal shapes, elliptical shapes and other geometric shapes can likewise be implemented. 
     In particular, the curvature of the lens  1912  can be chosen in manner that reduces phase differences between near-field wireless signals generated by the aperture  1903  of the dielectric antenna  1901 . The lens  1912  accomplishes this by applying location-dependent delays to propagating electromagnetic waves. Because of the curvature of the lens  1912 , the delays differ depending on where the electromagnetic waves emanate from at the aperture  1903 . For example, electromagnetic waves propagating by way of a center axis  1905  of the dielectric antenna  1901  will experience more delay through the lens  1912  than electromagnetic waves propagating radially away from the center axis  1905 . Electromagnetic waves propagating towards, for example, the outer edges of the aperture  1903  will experience minimal or no delay through the lens. Propagation delay increases as the electromagnetic waves get close to the center axis  1905 . Accordingly, a curvature of the lens  1912  can be configured so that near-field wireless signals have substantially similar phases. By reducing differences between phases of the near-field wireless signals, a width of far-field signals generated by the dielectric antenna  1901  is reduced, which in turn increases the intensity of the far-field wireless signals within the width of the main lobe, producing a relatively narrow beam pattern with high gain. 
     It should be noted that the lens  1912  can be configured in other lens configurations. For example, the lens  1912  can comprise concentric ridges  1914  configured to have a depth representative of a select wavelength factor. For example, a ridge can be configured to have a depth of one-quarter a wavelength of the electromagnetic waves propagating in the dielectric antenna  1901 . Such a configuration causes the electromagnetic wave reflected from one ridge to have a phase difference of 180 degrees relative to the electromagnetic wave reflected from an adjacent ridge. Consequently, the out of phase electromagnetic waves reflected from the adjacent risers  1916  substantially cancel, thereby reducing reflection and distortion caused thereby. 
     Turning now to  FIG. 19D , a block diagram illustrating an example, non-limiting embodiment of near-field signals  1928  and far-field signals  1930  emitted by the dielectric antenna  1901  having an elliptical aperture in accordance with various aspects described herein is shown. The cross section of the near-field beam pattern  1928  mimics the elliptical shape of the aperture  1903  of the dielectric antenna  1901 . The cross section of the far-field beam pattern  1930  have a rotational offset (approximately 90 degrees) that results from the elliptical shape of the near-field signals  1928 . The offset can be determined by applying a Fourier Transform to the near-field signals  1928 . While the cross section of the near-field beam pattern  1928  and the cross section of the far-field beam pattern  1930  are shown as nearly the same size in order to demonstrate the rotational effect, the actual size of the far-field beam pattern  1930  may increase with the distance from the dielectric antenna  1901 . 
     The elongated shape of the far-field signals  1930  and its orientation can prove useful when aligning a dielectric antenna  1901  in relation to a remotely located receiver configured to receive the far-field signals  1930 . The receiver can comprise one or more dielectric antennas coupled to a waveguide system such as described by the subject disclosure. The elongated far-field signals  1930  can increase the likelihood that the remotely located receiver will detect the far-field signals  1930 . In addition, the elongated far-field signals  1930  can be useful in situations where a dielectric antenna  1901  coupled to a gimbal assembly, or other actuated antenna mount (not shown) In particular, the elongated far-field signals  1930  can be useful in situations where such as gimbal mount only has two degrees of freedom for aligning the dielectric antenna  1901  in the direction of the receiver (e.g., yaw and pitch is adjustable but roll is fixed). 
     Although not shown, it will be appreciated that the dielectric antenna  1901  can have an integrated or attachable lens  1912  as previously described to increase an intensity of the far-fields signals  1930  by reducing phase differences in the near-field signals. 
     Turning now to  FIG. 19E , a block diagram of an example, non-limiting embodiment of a dielectric antenna  1901 ′ in accordance with various aspects described herein is shown.  FIG. 19E  depicts an array of pyramidal-shaped dielectric horn antennas  1901 ′, each having a corresponding aperture  1903 ′. Each antenna of the array of pyramidal-shaped dielectric horn antennas  1901 ′ can have a feedline  1902  with a corresponding feed point  1902 ″ that couples to each corresponding core  1852  of a plurality of cables  1850 . Each cable  1850  can be coupled to a different (or a same) waveguide system  1865 ′. The array of pyramidal-shaped dielectric horn antennas  1901 ′ can be used to transmit wireless signals having a plurality of spatial orientations. An array of pyramidal-shaped dielectric horn antennas  1901 ′ covering 360 degrees can enable a one or more waveguide systems  1865 ′ coupled to the antennas to perform omnidirectional communications with other communication devices or antennas of similar type. 
     The bidirectional propagation properties of electromagnetic waves previously described for the dielectric antenna  1901  of  FIG. 19A  are also applicable for electromagnetic waves propagating from the core  1852  to the feed point  1902 ″ guided by the feedline  1902  to the aperture  1903 ′ of the pyramidal-shaped dielectric horn antennas  1901 ′, and in the reverse direction. Similarly, the array of pyramidal-shaped dielectric horn antennas  1901 ′ can be substantially or entirely devoid of conductive external surfaces and internal conductive materials as discussed above. For example, in some embodiments, the array of pyramidal-shaped dielectric horn antennas  1901 ′ and their corresponding feed points  1902 ′ can be constructed of dielectric-only materials such as polyethylene or polyurethane materials or with only trivial amounts of conductive material that does not significantly alter the radiation pattern of the antenna. 
     It is further noted that each antenna of the array of pyramidal-shaped dielectric horn antennas  1901 ′ can have similar gain and electric field intensity maps as shown for the dielectric antenna  1901  in  FIG. 19B . Each antenna of the array of pyramidal-shaped dielectric horn antennas  1901 ′ can also be used for receiving wireless signals as previously described for the dielectric antenna  1901  of  FIG. 19A . In some embodiments, a single instance of a pyramidal-shaped dielectric horn antenna can be used. Similarly, multiple instances of the dielectric antenna  1901  of  FIG. 19A  can be used in an array configuration similar to the one shown in  FIG. 19E . 
     Turning now to  FIG. 19F , block diagrams of example, non-limiting embodiments of an array  1976  of dielectric antennas  1901  configurable for steering wireless signals in accordance with various aspects described herein is shown. The array  1976  of dielectric antennas  1901  can be conical shaped antennas  1901  or pyramidal-shaped dielectric antennas  1901 ′. To perform beam steering, a waveguide system coupled to the array  1976  of dielectric antennas  1901  can be adapted to utilize a circuit  1972  comprising amplifiers  1973  and phase shifters  1974 , each pair coupled to one of the dielectric antennas  1901  in the array  1976 . The waveguide system can steer far-field wireless signals from left to right (west to east) by incrementally increasing a phase delay of signals supplied to the dielectric antennas  1901 . 
     For example, the waveguide system can provide a first signal to the dielectric antennas of column  1  (“C 1 ”) having no phase delay. The waveguide system can further provide a second signal to column  2  (“C 2 ”), the second signal comprising the first signal having a first phase delay. The waveguide system can further provide a third signal to the dielectric antennas of column  3  (“C 3 ”), the third signal comprising the second signal having a second phase delay. Lastly, the waveguide system can provide a fourth signal to the dielectric antennas of column  4  (“C 4 ”), the fourth signal comprising the third signal having a third phase delay. These phase shifted signals will cause far-field wireless signals generated by the array to shift from left to right. Similarly, far-field signals can be steered from right to left (east to west) (“C 4 ” to “C 1 ”), north to south (“R 1 ” to “R 4 ”), south to north (“R 4 ” to “R 1 ”), and southwest to northeast (“C 1 -R 4 ” to “C 4 -R 1 ”). 
     Utilizing similar techniques beam steering can also be performed in other directions such as southwest to northeast by configuring the waveguide system to incrementally increase the phase of signals transmitted by the following sequence of antennas: “C 1 -R 4 ”, “C 1 -R 3 /C 2 -R 4 ”, “C 1 -R 2 /C 2 -R 3 /C 3 -R 4 ”, “C 1 -R 1 /C 2 -R 2 /C 3 -R 3 /C 4 -R 4 ”, “C 2 -R 1 /C 3 -R 2 /C 4 -R 3 ”, “C 3 -R 1 /C 4 -R 2 ”, “C 4 -R 1 ”. In a similar way, beam steering can be performed northeast to southwest, northwest to southeast, southeast to northwest, as well in other directions in three-dimensional space. Beam steering can be used, among other things, for aligning the array  1976  of dielectric antennas  1901  with a remote receiver and/or for directivity of signals to mobile communication devices. In some embodiments, a phased array  1976  of dielectric antennas  1901  can also be used to circumvent the use of the gimbal assembly of  FIG. 19M  or other actuated mount. While the foregoing has described beam steering controlled by phase delays, gain and phase adjustment can likewise be applied to the dielectric antennas  1901  of the phased array  1976  in a similar fashion to provide additional control and versatility in the formation of a desired beam pattern. 
     Turning now to  FIGS. 20A and 20B , block diagrams illustrating example, non-limiting embodiments of the cable  1850  of  FIG. 18A  used for inducing guided electromagnetic waves on power lines supported by utility poles. In one embodiment, as depicted in  FIG. 20A , a cable  1850  can be coupled at one end to a microwave apparatus that launches guided electromagnetic waves within one or more inner layers of cable  1850  utilizing, for example, the hollow waveguide  1808  shown in  FIG. 18A . The microwave apparatus can utilize a microwave transceiver such as shown in  FIG. 10  for transmitting or receiving signals from cable  1850 . The guided electromagnetic waves induced in the one or more inner layers of cable  1850  can propagate to an exposed stub of the cable  1850  located inside a horn antenna (shown as a dotted line in  FIG. 20A ) for radiating the electromagnetic waves via the horn antenna. The radiated signals from the horn antenna in turn can induce guided electromagnetic waves that propagate longitudinally on power line such as a medium voltage (MV) power line. In one embodiment, the microwave apparatus can receive AC power from a low voltage (e.g., 220V) power line. Alternatively, the horn antenna can be replaced with a stub antenna as shown in  FIG. 20B  to induce guided electromagnetic waves that propagate longitudinally on a power line such as the MV power line or to transmit wireless signals to other antenna system(s). 
     In an alternative embodiment, the hollow horn antenna shown in  FIG. 20A  can be replaced with a solid dielectric antenna such as the dielectric antenna  1901  of  FIG. 19A , or the pyramidal-shaped horn antenna  1901 ′ of  FIG. 19E . In this embodiment the horn antenna can radiate wireless signals directed to another horn antenna such as the bidirectional horn antennas  2040  shown in  FIG. 20C . In this embodiment, each horn antenna  2040  can transmit wireless signals to another horn antenna  2040  or receive wireless signals from the other horn antenna  2040  as shown in  FIG. 20C . Such an arrangement can be used for performing bidirectional wireless communications between antennas. Although not shown, the horn antennas  2040  can be configured with an electromechanical device to steer a direction of the horn antennas  2040 . 
     In alternate embodiments, first and second cables  1850 A′ and  1850 B′ can be coupled to the microwave apparatus and to a transformer  2052 , respectively, as shown in  FIGS. 20A and 20B . The first and second cables  1850 A′ and  1850 B′ can be represented by, for example, cable  1800  each modified to have a conductive core. A first end of the conductive core of the first cable  1850 A′ can be coupled to the microwave apparatus for propagating guided electromagnetic waves launched therein. A second end of the conductive core of the first cable  1850 A′ can be coupled to a first end of a conductive coil of the transformer  2052  for receiving the guided electromagnetic waves propagating in the first cable  1850 A′ and for supplying signals associated therewith to a first end of a second cable  1850 B′ by way of a second end of the conductive coil of the transformer  2052 . A second end of the second cable  1850 B′ can be coupled to the horn antenna of  FIG. 20A  or can be exposed as a stub antenna of  FIG. 20B  for inducing guided electromagnetic waves that propagate longitudinally on the MV power line. 
     In an embodiment where cable  1850 ,  1850 A′ and  1850 B′ each comprise multiple instances of transmission mediums  1800 , a poly-rod structure of antennas  1855  can be formed such as shown in  FIG. 18C . Each antenna  1855  can be coupled, for example, to a horn antenna assembly as shown in  FIG. 20A  or a pie-pan antenna assembly (not shown) for radiating multiple wireless signals. Alternatively, the antennas  1855  can be used as stub antennas in  FIG. 20B . The microwave apparatus of  FIGS. 20A-20B  can be configured to adjust the guided electromagnetic waves to beam steer the wireless signals emitted by the antennas  1855 . One or more of the antennas  1855  can also be used for inducing guided electromagnetic waves on a power line. 
     Turning now to  FIG. 20C , a block diagram of an example, non-limiting embodiment of a communication network  2000  in accordance with various aspects described herein is shown. In one embodiment, for example, the waveguide system  1602  of  FIG. 16A  can be incorporated into network interface devices (NIDs) such as NIDs  2010  and  2020  of  FIG. 20C . A NID having the functionality of waveguide system  1602  can be used to enhance transmission capabilities between customer premises  2002  (enterprise or residential) and a pedestal  2004  (sometimes referred to as a service area interface or SAI). 
     In one embodiment, a central office  2030  can supply one or more fiber cables  2026  to the pedestal  2004 . The fiber cables  2026  can provide high-speed full-duplex data services (e.g., 1-100 Gbps or higher) to mini-DSLAMs  2024  located in the pedestal  2004 . The data services can be used for transport of voice, internet traffic, media content services (e.g., streaming video services, broadcast TV), and so on. In prior art systems, mini-DSLAMs  2024  typically connect to twisted pair phone lines (e.g., twisted pairs included in category 5e or Cat. 5e unshielded twisted-pair (UTP) cables that include an unshielded bundle of twisted pair cables, such as 24 gauge insulated solid wires, surrounded by an outer insulating sheath), which in turn connect to the customer premises  2002  directly. In such systems, DSL data rates taper off at 100 Mbps or less due in part to the length of legacy twisted pair cables to the customer premises  2002  among other factors. 
     The embodiments of  FIG. 20C , however, are distinct from prior art DSL systems. In the illustration of  FIG. 20C , a mini-DSLAM  2024 , for example, can be configured to connect to NID  2020  via cable  1850  (which can represent in whole or in part any of the cable embodiments described in relation to  FIGS. 18A and 18B  singly or in combination). Utilizing cable  1850  between customer premises  2002  and a pedestal  2004 , enables NIDs  2010  and  2020  to transmit and receive guide electromagnetic waves for uplink and downlink communications. Based on embodiments previously described, cable  1850  can be exposed to rain, or can be buried without adversely affecting electromagnetic wave propagation either in a downlink path or an uplink path so long as the electric field profile of such waves in either direction is confined at least in part or entirely within inner layers of cable  1850 . In the present illustration, downlink communications represents a communication path from the pedestal  2004  to customer premises  2002 , while uplink communications represents a communication path from customer premises  2002  to the pedestal  2004 . In an embodiment where cable  1850  includes an inner conductor, cable  1850  can also serve the purpose of supplying power to the NID  2010  and  2020  and other equipment of the customer premises  2002  and the pedestal  2004 . 
     In customer premises  2002 , DSL signals can originate from a DSL modem  2006  (which may have a built-in router and which may provide wireless services such as WiFi to user equipment shown in the customer premises  2002 ). The DSL signals can be supplied to NID  2010  by a twisted pair phone  2008 . The NID  2010  can utilize the integrated waveguide  1602  to launch within cable  1850  guided electromagnetic waves  2014  directed to the pedestal  2004  on an uplink path. In the downlink path, DSL signals generated by the mini-DSLAM  2024  can flow through a twisted pair phone line  2022  to NID  2020 . The waveguide system  1602  integrated in the NID  2020  can convert the DSL signals, or a portion thereof, from electrical signals to guided electromagnetic waves  2014  that propagate within cable  1850  on the downlink path. To provide full duplex communications, the guided electromagnetic waves  2014  on the uplink can be configured to operate at a different carrier frequency and/or a different modulation approach than the guided electromagnetic waves  2014  on the downlink to reduce or avoid interference. Additionally, on the uplink and downlink paths, the guided electromagnetic waves  2014  are guided by a core section of cable  1850 , as previously described, and such waves can be configured to have a field intensity profile that confines the guide electromagnetic waves in whole or in part in the inner layers of cable  1850 . Although the guided electromagnetic waves  2014  are shown outside of cable  1850 , the depiction of these waves is for illustration purposes only. For this reason, the guided electromagnetic waves  2014  are drawn with “hash marks” to indicate that they are guided by the inner layers of cable  1850 . 
     On the downlink path, the integrated waveguide system  1602  of NID  2010  receives the guided electromagnetic waves  2014  generated by NID  2020  and converts them back to DSL signals conforming to the requirements of the DSL modem  2006 . The DSL signals are then supplied to the DSL modem  2006  via a set of twisted pair wires of phone line  2008  for processing. Similarly, on the uplink path, the integrated waveguide system  1602  of NID  2020  receives the guided electromagnetic waves  2014  generated by NID  2010  and converts them back to DSL signals conforming to the requirements of the mini-DSLAM  2024 . The DSL signals are then supplied to the mini-DSLAM  2024  via a set of twisted pair wires of phone line  2022  for processing. Because of the short length of phone lines  2008  and  2022 , the DSL modem  2006  and the mini-DSLAM  2024  can send and receive DSL signals between themselves on the uplink and downlink at very high speeds (e.g., 1 Gbps to 60 Gbps or more). Consequently, the uplink and downlink paths can in most circumstances exceed the data rate limits of traditional DSL communications over twisted pair phone lines. 
     Typically, DSL devices are configured for asymmetric data rates because the downlink path usually supports a higher data rate than the uplink path. However, cable  1850  can provide much higher speeds both on the downlink and uplink paths. With a firmware update, a legacy DSL modem  2006  such as shown in  FIG. 20C  can be configured with higher speeds on both the uplink and downlink paths. Similar firmware updates can be made to the mini-DSLAM  2024  to take advantage of the higher speeds on the uplink and downlink paths. Since the interfaces to the DSL modem  2006  and mini-DSLAM  2024  remain as traditional twisted pair phone lines, no hardware change is necessary for a legacy DSL modem or legacy mini-DSLAM other than firmware changes and the addition of the NIDs  2010  and  2020  to perform the conversion from DSL signals to guided electromagnetic waves  2014  and vice-versa. The use of NIDs enables a reuse of legacy modems  2006  and mini-DSLAMs  2024 , which in turn can substantially reduce installation costs and system upgrades. For new construction, updated versions of mini-DSLAMs and DSL modems can be configured with integrated waveguide systems to perform the functions described above, thereby eliminating the need for NIDs  2010  and  2020  with integrated waveguide systems. In this embodiment, an updated version of modem  2006  and updated version of mini-DSLAM  2024  would connect directly to cable  1850  and communicate via bidirectional guided electromagnetic wave transmissions, thereby averting a need for transmission or reception of DSL signals using twisted pair phone lines  2008  and  2022 . 
     In an embodiment where use of cable  1850  between the pedestal  2004  and customer premises  2002  is logistically impractical or costly, NID  2010  can be configured instead to couple to a cable  1850 ′ (similar to cable  1850  of the subject disclosure) that originates from a waveguide  108  on a utility pole  118 , and which may be buried in soil before it reaches NID  2010  of the customer premises  2002 . Cable  1850 ′ can be used to receive and transmit guided electromagnetic waves  2014 ′ between the NID  2010  and the waveguide  108 . Waveguide  108  can connect via waveguide  106 , which can be coupled to base station  104 . Base station  104  can provide data communication services to customer premises  2002  by way of its connection to central office  2030  over fiber  2026 ′. Similarly, in situations where access from the central office  2030  to pedestal  2004  is not practical over a fiber link, but connectivity to base station  104  is possible via fiber link  2026 ′, an alternate path can be used to connect to NID  2020  of the pedestal  2004  via cable  1850 ″ (similar to cable  1850  of the subject disclosure) originating from pole  116 . Cable  1850 ″ can also be buried before it reaches NID  2020 . 
     Turning now to  FIGS. 20D and 20E , diagrams of example, non-limiting embodiments of antenna mounts that can be used in the communication network  2000  of  FIG. 20C  (or other suitable communication networks) in accordance with various aspects described herein are shown. In some embodiments, an antenna mount  2053  can be coupled to a medium voltage power line by way of an inductive power supply that supplies energy to one or more waveguide systems (not shown) integrated in the antenna mount  2053  as depicted in  FIG. 20D . The antenna mount  2053  can include an array of dielectric antennas  1901  (e.g.,  16  antennas) such as shown by the top and side views depicted in  FIG. 20F . The dielectric antennas  1901  shown in  FIG. 20F  can be small in dimension as illustrated by a picture comparison between groups of dielectric antennas  1901  and a conventional ballpoint pen. In other embodiments, a pole mounted antenna  2054  can be used as depicted in  FIG. 20D . In yet other embodiments, an antenna mount can be attached to a pole with an arm assembly. In other embodiments, an antenna mount can be placed on a top portion of a pole coupled to a cable  1800  or  1836  such as the cables as described in the subject disclosure. 
     The array of dielectric antennas  1901  of the antenna mount of  FIG. 20D  can include one or more waveguide systems as described in the subject disclosure by way of  FIGS. 1-20 . The waveguide systems can be configured to perform beam steering with the array of dielectric antennas  1901  (for transmission or reception of wireless signals). Alternatively, each dielectric antenna  1901  can be utilized as a separate sector for receiving and transmitting wireless signals. In other embodiments, the one or more waveguide systems integrated in the antenna mount of  FIG. 20D  can be configured to utilize combinations of the dielectric antennas  1901  in a wide range of multi-input multi-output (MIMO) transmission and reception techniques. The one or more waveguide systems integrated in the antenna mount of  FIG. 20D  can also be configured to apply communication techniques such as SISO, SIMO, MISO, SISO, signal diversity (e.g., frequency, time, space, polarization, or other forms of signal diversity techniques), and so on, with any combination of the dielectric antennas  1901  in any of the antenna mount of  FIG. 20D . In yet other embodiments, the antenna mount of  FIG. 20D  can be adapted with two or more stacks of the antenna arrays shown in  FIG. 20E . 
       FIGS. 21A and 21B  describe embodiments for downlink and uplink communications. Method  2100  of  FIG. 21A  can begin with step  2102  where electrical signals (e.g., DSL signals) are generated by a DSLAM (e.g., mini-DSLAM  2024  of pedestal  2004  or from central office  2030 ), which are converted to guided electromagnetic waves  2014  at step  2104  by NID  2020  and which propagate on a transmission medium such as cable  1850  for providing downlink services to the customer premises  2002 . At step  2108 , the NID  2010  of the customer premises  2002  converts the guided electromagnetic waves  2014  back to electrical signals (e.g., DSL signals) which are supplied at step  2110  to customer premises equipment (CPE) such as DSL modem  2006  over phone line  2008 . Alternatively, or in combination, power and/or guided electromagnetic waves  2014 ′ can be supplied from a power line  1850 ′ of a utility grid (having an inner waveguide as illustrated in  FIG. 18G or 18H ) to NID  2010  as an alternate or additional downlink (and/or uplink) path. 
     At step  2122  of method  2120  of  FIG. 21B , the DSL modem  2006  can supply electrical signals (e.g., DSL signals) via phone line  2008  to NID  2010 , which in turn at step  2124 , converts the DSL signals to guided electromagnetic waves directed to NID  2020  by way of cable  1850 . At step  2128 , the NID  2020  of the pedestal  2004  (or central office  2030 ) converts the guided electromagnetic waves  2014  back to electrical signals (e.g., DSL signals) which are supplied at step  2129  to a DSLAM (e.g., mini-DSLAM  2024 ). Alternatively, or in combination, power and guided electromagnetic waves  2014 ′ can be supplied from a power line  1850 ′ of a utility grid (having an inner waveguide as illustrated in  FIG. 18G or 18H ) to NID  2020  as an alternate or additional uplink (and/or downlink) path. 
     Turning now to  FIG. 21C , a block diagram  2151  illustrating an example, non-limiting embodiment of electric field characteristics of a hybrid wave versus a Goubau wave in accordance with various aspects described herein is shown. Diagram  2158  shows a distribution of energy between HE11 mode waves and Goubau waves for an insulated conductor. The energy plots of diagram  2158  assume that the amount of power used to generate the Goubau waves is the same as the HE11 waves (i.e., the area under the energy curves is the same). In the illustration of diagram  2158 , Goubau waves have a steep drop in power when Goubau waves extend beyond the outer surface of an insulated conductor, while HE11 waves have a substantially lower drop in power beyond the insulation layer. Consequently, Goubau waves have a higher concentration of energy near the insulation layer than HE 11 waves. Diagram  2167  depicts similar Goubau and HE11 energy curves when a water film is present on the outer surface of the insulator. The difference between the energy curves of diagrams  2158  and  2167  is that the drop in power for the Goubau and the HE11 energy curves begins on an outer edge of the insulator for diagram  2158  and on an outer edge of the water film for diagram  2167 . The energy curves diagrams  2158  and  2167 , however, depict the same behavior. That is, the electric fields of Goubau waves are tightly bound to the insulation layer, which when exposed to water results in greater propagation losses than electric fields of HE11 waves having a higher concentration outside the insulation layer and the water film. These properties are depicted in the HE11 and Goubau diagrams  2168  and  2159 , respectively. 
     By adjusting an operating frequency of HE11 waves, e-fields of HE11 waves can be configured to extend substantially above a thin water film as shown in block diagram  2169  of  FIG. 21D  having a greater accumulated field strength in areas in the air when compared to fields in the insulator and a water layer surrounding the outside of the insulator.  FIG. 21D  depicts a wire having a radius of 1 cm and an insulation radius of 1.5 cm with a dielectric constant of 2.25. As the operating frequency of HE11 waves is reduced, the e-fields extend outwardly expanding the size of the wave mode. At certain operating frequencies (e.g., 3 GHz) the wave mode expansion can be substantially greater than the diameter of the insulated wire and any obstructions that may be present on the insulated wire. 
     By having e-fields that are perpendicular to a water film and by placing most of its energy outside the water film, HE11 waves have less propagation loss than Goubau waves when a transmission medium is subjected to water or other obstructions. Although Goubau waves have radial e-fields which are desirable, the waves are tightly coupled to the insulation layer, which results in the e-fields being highly concentrated in the region of an obstruction. Consequently, Goubau waves are still subject to high propagation losses when an obstruction such as a water film is present on the outer surface of an insulated conductor. 
     Turning now to  FIGS. 22A and 22B , block diagrams illustrating example, non-limiting embodiments of a waveguide system  2200  for launching hybrid waves in accordance with various aspects described herein is shown. The waveguide system  2200  can comprise probes  2202  coupled to a slideable or rotatable mechanism  2204  that enables the probes  2202  to be placed at different positions or orientations relative to an outer surface of an insulated conductor  2208 . The mechanism  2204  can comprise a coaxial feed  2206  or other coupling that enables transmission of electromagnetic waves by the probes  2202 . The coaxial feed  2206  can be placed at a position on the mechanism  2204  so that the path difference between the probes  2202  is one-half a wavelength or some odd integer multiple thereof. When the probes  2202  generate electromagnetic signals of opposite phase, electromagnetic waves can be induced on the outer surface of the insulated conductor  2208  having a hybrid mode (such as an HE11 mode). 
     The mechanism  2204  can also be coupled to a motor or other actuator (not shown) for moving the probes  2202  to a desirable position. In one embodiment, for example, the waveguide system  2200  can comprise a controller that directs the motor to rotate the probes  2202  (assuming they are rotatable) to a different position (e.g., east and west) to generate electromagnetic waves that have a horizontally polarized HE11 mode. To guide the electromagnetic waves onto the outer surface of the insulated conductor  2208 , the waveguide system  2200  can further comprise a tapered horn  2210  shown in  FIG. 22B . The tapered horn  2210  can be coaxially aligned with the insulated conductor  2208 . To reduce the cross-sectional dimension of the tapered horn  2210 , an additional insulation layer (not shown) can placed on the insulated conductor  2208 . The additional insulation layer can be similar to the tapered insulation layer  1879  shown in  FIGS. 18G and 18H . The additional insulation layer can have a tapered end that points away from the tapered horn  2210 . The tapered insulation layer  1879  can reduce a size of an initial electromagnetic wave launched according to an HE11 mode. As the electromagnetic waves propagate towards the tapered end of the insulation layer, the HE11 mode expands until it reaches its full size. In other embodiments, the waveguide system  2200  may not need to use the tapered insulation layer  1879 . 
     HE11 mode waves can be used to mitigate obstructions such as rain water. For example, suppose that rain water has caused a water film to surround an outer surface of the insulated conductor  2208 . Further assume that water droplets have collected at the bottom of the insulated conductor  2208 . The water film occupies a small fraction of the total HE11 wave. Also, by having horizontally polarized HE11 waves, the water droplets are in a least-intense area of the HE11 waves reducing losses caused by the droplets. Consequently, the HE11 waves experience much lower propagation losses than Goubau waves or waves having a mode that is tightly coupled to the insulated conductor  2208  and thus greater energy in the areas occupied by the water. 
     It is submitted that the waveguide system  2200  of  FIGS. 22A-22B  can be replaced with other waveguide systems of the subject disclosure capable of generating electromagnetic waves having an HE mode. For example, the waveguide system  1865 ′ of  FIG. 18K  can be configured to generate electromagnetic waves having an HE mode. In an embodiment, two or more MMICs  1870  of the waveguide system  1865 ′ can be configured to generate electromagnetic waves of opposite phase to generate polarized e-fields such as those present in an HE mode. In another embodiment, different pairs of MMICs  1870  can be selected to generate HE waves that are polarized at different spatial positions (e.g., north and south, west and east, northwest and southeast, northeast and southeast, or other sub-fractional coordinates). Additionally, the waveguide systems of  FIGS. 18D-18K  can be configured to launch electromagnetic waves having an HE mode onto the core  1852  of one or more embodiments of cable  1850  suitable for propagating HE mode waves. 
     Although HE waves can have desirable characteristics for mitigating obstructions on a transmission medium, it is submitted that certain wave modes having a cutoff frequency (e.g., TE modes, TM modes or combinations thereof) may also exhibit waves that are sufficiently large and have polarized e-fields that are orthogonal (or approximately orthogonal) to a region of an obstruction enabling their use for mitigating propagation losses caused by the obstruction. 
     Turning to the illustration of  FIG. 23 , the waveguide  2522  covers a first region  2506  of a core  2528 . Within the first region  2506 , waveguide  2522  has an outer surface  2522 A and an inner surface  2523 . The inner surface  2523  of the waveguide  2522  can be constructed from a metallic material or other material that reflects electromagnetic waves and thereby enables the waveguide  2522  to be configured at step  2404  to guide the first electromagnetic wave  2502  towards the core  2528 . The core  2528  can comprise a dielectric core (as described in the subject disclosure) that extends to the inner surface  2523  of the waveguide  2522 . In other embodiments, the dielectric core can be surrounded by cladding (such as shown in  FIG. 18A ), whereby the cladding extends to the inner surface  2523  of the waveguide  2522 . In yet other embodiments, the core  2528  can comprise an insulated conductor, where the insulation extends to the inner surface  2523  of the waveguide  2522 . In this embodiment, the insulated conductor can be a power line, a coaxial cable, or other types of insulated conductors. 
     In the first region  2506 , the core  2528  comprises an interface  2526  for receiving the first electromagnetic wave  2502 . In one embodiment, the interface  2526  of the core  2528  can be configured to reduce reflections of the first electromagnetic wave  2502 . In one embodiment, the interface  2526  can be a tapered structure to reduce reflections of the first electromagnetic wave  2502  from a surface of the core  2528 . Other structures can be used for the interface  2526 . For example, the interface  2526  can be partially tapered with a rounded point. Accordingly, any structure, configuration, or adaptation of the interface  2526  that can reduced reflections of the first electromagnetic wave  2502  is contemplated by the subject disclosure. The first electromagnetic wave  2502  induces (or otherwise generates) a second electromagnetic wave  2504  that propagates within the core  2528  in the first region  2506  covered by the waveguide  2522 . The inner surface  2523  of the waveguide  2522  confines the second electromagnetic wave  2504  within the core  2528 . 
     A second region  2508  of the core  2528  is not covered by the waveguide  2522 , and is thereby exposed to the environment (e.g., air). In the second region  2508 , the second electromagnetic wave  2504  expands outwardly beginning from the discontinuity between the edge of the waveguide  2522  and the exposed core  2528 . To reduce the radiation into the environment from the second electromagnetic wave  2504 , the core  2528  can be configured to have a tapered structure  2520 . As the second electromagnetic wave  2504  propagates along the tapered structure  2520 , the second electromagnetic wave  2504  remains substantially bound to the tapered structure  2520  thereby reducing radiation losses. The tapered structure  2520  ends at a transition from the second region  2508  to a third region  2510 . In the third region, the core has a cylindrical structure  2529  having a diameter equal to the endpoint of the tapered structure  2520  at the juncture between the second region  2508  and the third region  2510 . In the third region  2510  of the core  2528 , the second electromagnetic wave  2504  experiences a low propagation loss. In one embodiment, this can be accomplished by selecting a diameter of the core  2528  that enables the second electromagnetic wave  2504  to be loosely bound to the outer surface of the core  2528  in the third region  2510 . Alternatively, or in combination, propagation losses of the second electromagnetic wave  2504  can be reduced by configuring the MMICs  2524  to adjust a wave mode, wave length, operating frequency, or other operational parameter of the first electromagnetic wave  2502 . 
       FIG. 24  illustrates a portion of the waveguide  2522  of  FIG. 23A  depicted as a cylindrical ring (that does not show the MMICs  2524  or the tapered structure  2526  of  FIG. 23A ). In the simulations, a first electromagnetic wave is injected at the endpoint of the core  2528  shown in  FIG. 24 . The simulation assumes no reflections of the first electromagnetic wave based on an assumption that a tapered structure  2526  (or other suitable structure) is used to reduce such reflections. The simulations are shown as two longitudinal cross-sectional views of the core  2528  covered in part by waveguide section  2523 A, and an orthogonal cross-sectional view of the core  2528 . In the case of the longitudinal cross-sectional views, one of the illustrations is a blown up view of a portion of the first illustration. 
     As can be seen from the simulations, electromagnetic wave fields  2532  of the second electromagnetic wave  2504  are confined within the core  2528  by the inner surface  2523  of the waveguide section  2523 A. As the second electromagnetic wave  2504  enters the second region  2508  (no longer covered by the waveguide section  2523 A), the tapered structure  2520  reduces radiation losses of the electromagnetic wave fields  2532  as it expands over the outer tapered surface of the core  2528 . As the second electromagnetic wave  2504  enters the third region  2510 , the electromagnetic wave fields  2532  stabilize and thereafter remain loosely coupled to the core  2528  (depicted in the longitudinal and orthogonal cross-sectional views), which reduces propagation losses. 
       FIG. 23B  provides an alternative embodiment to the tapered structure  2520  in the second region  2508 . The tapered structure  2520  can be avoided by extending the waveguide  2522  into the second region  2508  with a tapered structure  2522 B and maintaining the diameter of the core  2528  throughout the first, second and third regions  2506 ,  2508  and  2510  of the core  2528  as depicted in  FIG. 23B . The horn structure  2522 B can be used to reduce radiation losses of the second electromagnetic wave  2504  as the second electromagnetic wave  2504  transitions from the first region  2506  to the second region  2508 . In the third region  2510 , the core  2528  is exposed to the environment. As noted earlier, the core  2528  is configured in the third region  2510  to reduce propagation losses by the second electromagnetic wave  2504 . In one embodiment, this can be accomplished by selecting a diameter of the core  2528  that enables the second electromagnetic wave  2504  to be loosely bound to the outer surface of the core  2528  in the third region  2510 . Alternatively, or in combination, propagation losses of the second electromagnetic wave  2504  can be reduced by adjusting a wave mode, wave length, operating frequency, or other performance parameter of the first electromagnetic wave  2502 . 
     The waveguides  2522  of  FIGS. 23A and 23B  can also be adapted for receiving electromagnetic waves. For example, the waveguide  2522  of  FIG. 23A  can be adapted to receive an electromagnetic wave at step  2412 . This can be represented by an electromagnetic wave  2504  propagating in the third region  2510  from east to west (orientation shown at bottom right of  FIGS. 23A-23B ) towards the second region  2508 . Upon reaching the second region  2508 , the electromagnetic wave  2504  gradually becomes more tightly coupled to the tapered structure  2520 . When it reaches the boundary between the second region  2508  and the first region  2506  (i.e., the edge of the waveguide  2522 ), the electromagnetic wave  2504  propagates within the core  2528  confined by the inner surface  2523  of the waveguide  2522 . Eventually the electromagnetic wave  2504  reaches an endpoint of the tapered interface  2526  of the core  2528  and radiates as a new electromagnetic wave  2502  which is guided by the inner surface  2523  of the waveguide  2522 . 
     One or more antennas of the MMICs  2524  can be configured to receive the electromagnetic wave  2502  thereby converting the electromagnetic wave  2502  to an electrical signal at step  2414  which can be processed by a processing device (e.g., a receiver circuit and microprocessor). To prevent interference between electromagnetic waves transmitted by the MMICs  2524 , a remote waveguide system that transmitted the electromagnetic wave  2504  that is received by the waveguide  2522  of  FIG. 23A  can be adapted to transmit the electromagnetic wave  2504  at a different operating frequency, different wave mode, different phase, or other adjustable operational parameter to avoid interference. Electromagnetic waves can be received by the waveguide  2522  of  FIG. 23B  in a similar manner as described above. 
     Turning now to  FIG. 23C , the waveguide  2522  of  FIG. 23B  can be adapted to support transmission mediums  2528  that have no endpoints such as shown in  FIG. 23C . In this illustration, the waveguide  2522  comprises a chamber  2525  in a first region  2506  of the core  2528 . The chamber  2525  creates a gap  2527  between an outer surface  2521  of the core  2528  and the inner surface  2523  of the waveguide  2522 . The gap  2527  provides sufficient room for placement of the MMICs  2524  on the inner surface  2523  of the waveguide  2522 . To enable the waveguide  2522  to receive electromagnetic waves from either direction, the waveguide  2522  can be configured with symmetrical regions:  2508  and  2508 ′,  2510  and  2510 ′, and  2512 , and  2512 ′. In the first region  2506 , the chamber  2525  of the waveguide  2522  has two tapered structures  2522 B′ and  2522 B″. These tapered structures  2522 B′ and  2522 B″ enable an electromagnetic wave to gradually enter or exit the chamber  2525  from either direction of the core  2528 . The MMICs  2524  can be configured with directional antennas to launch a first electromagnetic wave  2502  directed from east-to-west or from west-to-east in relation to the longitudinal view of the core  2528 . Similarly, the directional antennas of the MMICs  2524  can be configured to receive an electromagnetic waves propagating longitudinally on the core  2528  from east-to-west or from west-to-east. The process for transmitting electromagnetic waves is similar to that described for  FIG. 23B  depending on whether the directional antennas of the MMICs  2524  are transmitting from east-to-west or from west-to-east. 
     Although not shown, the waveguide  2522  of  FIG. 23C  can be configured with a mechanism such as one or more hinges that enable splitting the waveguide  2522  into two parts that can be separated. The mechanism can be used to enable installation of the waveguide  2522  onto a core  2528  without endpoints. Other mechanisms for installation of the waveguide  2522  of  FIG. 23C  on a core  2528  are contemplated by the subject disclosure. For example, the waveguide  2522  can be configured with a slot opening that spans the entire waveguide structure longitudinally. In a slotted design of the waveguide  2522 , the regions  2522 C′ and  2522 C of the waveguide  2522  can be configured so that the inner surface  2523  of the waveguide  2522  is tightly coupled to the outer surface of the core  2528 . The tight coupling between the inner surface  2523  of the waveguide  2522  the outer surface of the core  2528  prevents sliding or movement of the waveguide  2522  relative to the core  2528 . A tight coupling in the regions  2522 C′ and  2522 C can also be applied to a hinged design of the waveguide  2522 . 
     The waveguides  2522  shown in  FIGS. 23A, 23B and 25C  can be adapted to perform one or more embodiments described in other figures of the subject disclosure. Accordingly, it is contemplated that such embodiments can be applied to the waveguide  2522  of  FIGS. 23A, 23B and 23C . Additionally, any adaptations in the subject disclosure of a core can be applied to the waveguide  2522  of  FIGS. 23A, 23B and 23C . 
     It is further noted that the waveguide launchers  2522  of  FIGS. 23A-23C  and/or other waveguide launchers described and shown in the figures of the subject disclosure (e.g.,  FIGS. 7-14, 18D-18K, 22A-22B, 23A-23C, 24  and other drawings) and any methods thereof can be adapted to generate along a transmission medium having an outer surface composed of, for example, a dielectric material (e.g., insulation, oxidation, or other material with dielectric properties) a single wave mode or combination of wave modes that reduce propagation losses when propagating through a substance, such as a liquid (e.g., water produced by humidity, snow, dew, sleet and/or rain), disposed on the outer surface of the transmission medium. 
     Referring now to  FIG. 25A , there is illustrated a diagram of an example, non-limiting embodiment of a waveguide device  2522  in accordance with various aspects described herein. In the illustration of  FIG. 25A , the waveguide device  2522  is coupled to a transmission medium  2542  comprising a conductor  2543  and insulation layer  2543 , which together form an insulated conductor. Although not shown, the waveguide device  2522  can be constructed in two halves, which can be connected together at one longitudinal end with one or more mechanical hinges to enable opening a longitudinal edge at an opposite end of the one or more hinges for placement of the waveguide device  2522  over the transmission medium  2542 . Once placed, one or more latches at the longitudinal edge opposite the one or more hinges can be used to secure the waveguide device  2522  to the transmission medium  2542 . Other embodiments for coupling the waveguide device  2522  to the transmission medium  2542  can be used and are therefore contemplated by the subject disclosure. 
     The chamber  2525  of the waveguide device  2522  of  FIG. 25A  includes a dielectric material  2544 ′. The dielectric material  2544 ′ in the chamber  2525  can have a dielectric constant similar to the dielectric constant of the dielectric layer  2544  of the insulated conductor. Additionally, a disk  2525 ′ having a center-hole 2525″ can be used to divide the chamber  2525  in two halves for transmission or reception of electromagnetic waves. The disk  2525 ′ can be constructed of a material (e.g., carbon, metal or other reflective material) that does not allow electromagnetic waves to progress between the halves of the chamber  2525 . The MMICs  2524 ′ can be located inside the dielectric material  2544 ′ of the chamber  2525  as shown in  FIG. 25A . Additionally, the MMICs  2524 ′ can be located near an outer surface of the dielectric layer  2543  of the transmission medium  2542 .  FIG. 25A  shows an expanded view  2524 A′ of an MMIC  2524 ′ that includes an antenna  2524 B′ (such as a monopole antenna, dipole antenna or other antenna) that can be configured to be longitudinally aligned with the outer surface of the dielectric layer  2543  of the transmission medium  2542 . The antenna  2524 B′ can be configured to radiate signals that have a longitudinal electric field directed east or west as will be discussed shortly. It will be appreciated that other antenna structures that can radiate signals that have a longitudinal electric field can be used in place of the dipole antenna  2524 B′ of  FIG. 25A . 
     It will be appreciated that although two MMICs  2524 ′ are shown in each half of the chambers  2525  of the waveguide device  2522 , more MMICs can be used. For example,  FIG. 18K  shows a transverse cross-sectional view of a cable (such as the transmission medium  2542 ) surrounded by a waveguide device with 8 MMICs located in positions: north, south, east, west, northeast, northwest, southeast, and southwest. The two MMICs  2524 ′ shown in  FIG. 25A  can be viewed, for illustration purposes, as MMICs  2524 ′ located in the north and south positions shown in  FIG. 18K . The waveguide device  2522  of  FIG. 25A  can be further configured with MMICs  2524 ′ at western and eastern positions as shown in  FIG. 18K . Additionally, the waveguide device  2522  of  FIG. 25A  can be further configured with MMICs at northwestern, northeastern, southwestern and southeastern positions as shown in  FIG. 18K . Accordingly, the waveguide device  2522  can be configured with more than the 2 MMICs shown in  FIG. 25A . 
     With this in mind, attention is now directed to  FIGS. 25B, 25C, 25D , which illustrate diagrams of example, non-limiting embodiments of wave modes and electric field plots in accordance with various aspects described herein.  FIG. 25B  illustrates the electric fields of a TM01 wave mode. The electric fields are illustrated in a transverse cross-sectional view (top) and a longitudinal cross-sectional view (below) of a coaxial cable having a center conductor with an external conductive shield separated by insulation.  FIG. 25C  illustrates the electric fields of a TM11 wave mode. The electric fields are also illustrated in a transverse cross-sectional view and a longitudinal cross-sectional view of a coaxial cable having a center conductor with an external conductive shield separated by an insulation.  FIG. 25D  further illustrates the electric fields of a TM21 wave mode. The electric fields are illustrated in a transverse cross-sectional view and a longitudinal cross-sectional view of a coaxial cable having a center conductor with an external conductive shield separated by an insulation. 
     As shown in the transverse cross-sectional view, the TM01 wave mode has circularly symmetric electric fields (i.e., electric fields that have the same orientation and intensity at different azimuthal angles), while the transverse cross-sectional views of the TM11 and TM21 wave modes shown in  FIGS. 25C-25D , respectively, have non-circularly symmetric electric fields (i.e., electric fields that have different orientations and intensities at different azimuthal angles). Although the transverse cross-sectional views of the TM11 and TM21 wave modes have non-circularly symmetric electric fields, the electric fields in the longitudinal cross-sectional views of the TM01, TM11 and TM21 wave modes are substantially similar with the exception that that the electric field structure of the TM11 wave mode has longitudinal electric fields above the conductor and below the conductor that point in opposite longitudinal directions, while the longitudinal electric fields above the conductor and below the conductor for the TM01 and TM21 wave modes point in the same longitudinal direction. 
     The longitudinal cross-sectional views of the coaxial cable of  FIGS. 25B, 25C and 25D  can be said to have a similar structural arrangement to the longitudinal cross-section of the waveguide device  2522  in region  2506 ′ shown in  FIG. 25A . Specifically, in  FIGS. 25B, 25C and 25D  the coaxial cable has a center conductor and a shield separated by insulation, while region  2506 ′ of the waveguide device  2522  has a center conductor  2543 , a dielectric layer  2544 , covered by the dielectric material  2544 ′ of the chamber  2525 , and shielded by the reflective inner surface  2523  of the waveguide device  2522 . The coaxial configuration in region  2506 ′ of the waveguide device  2522  continues in the tapered region  2506 ″ of the waveguide device  2522 . Similarly, the coaxial configuration continues in regions  2508  and  2510  of the waveguide device  2522  with the exception that no dielectric material  2544 ′ is present in these regions other than the dielectric layer  2544  of the transmission medium  2542 . At the outer region  2512 , the transmission medium  2542  is exposed to the environment (e.g., air) and thus the coaxial configuration is no longer present. 
     As noted earlier, the electric field structure of a TM01 wave mode is circularly symmetric in a transverse cross-sectional view of the coaxial cable shown in  FIG. 25B . For illustration purposes, it will be assumed that the waveguide device  2522  of  FIG. 25A  has 4 MMICs located in northern, southern, western and eastern locations as depicted in  FIG. 18K . In this configuration, and with an understanding of the longitudinal and transverse electric field structures of the TM01 wave mode shown in  FIG. 25B , the 4 MMICs  2524 ′ of the waveguide device  2522  in  FIG. 25A  can be configured to launch from a common signal source a TM01 wave mode on the transmission medium  2542 . This can be accomplished by configuring the north, south, east and west MMICs  2524 ′ to launch wireless signals with the same phase (polarity). The wireless signals generated by the 4 MMICs  2524 ′ combine via superposition of their respective electric fields in the dielectric material  2544 ′ of the chamber  2525  and the dielectric layer  2544  (since both dielectric materials have similar dielectric constants) to form a TM01 electromagnetic wave  2502 ′ bound to these dielectric materials with the electric field structure shown in longitudinal and transverse views of  FIG. 25B . 
     The electromagnetic wave  2502 ′ having the TM01 wave mode in turn propagates toward the tapered structure  2522 B of the waveguide device  2522  and thereby becomes an electromagnetic wave  2504 ′ embedded within the dielectric layer  2544  of the transmission medium  2542 ′ in region  2508 . In the tapered horn section  2522 D the electromagnetic wave  2504 ′ having the TM01 wave mode expands in region  2510  and eventually exits the waveguide device  2522  without change to the TM01 wave mode. 
     In another embodiment, the waveguide device  2522  can be configured to launch a TM11 wave mode having a vertical polarity in region  2506 ′. This can be accomplished by configuring the MMIC  2524 ′ in the northern position to radiate from a signal source a first wireless signal having a phase (polarity) opposite to the phase (polarity) of a second wireless signal radiated from the same signal source by the southern MMIC  2524 ′. These wireless signals combine via superposition of their respective electric fields to form an electromagnetic wave having a TM11 wave mode (vertically polarized) bound to the dielectric materials  2544 ′ and  2544  with the electric field structures shown in the longitudinal and transverse cross-sectional views shown in  FIG. 25C . Similarly, the waveguide device  2522  can be configured to launch a TM11 wave mode having a horizontal polarity in region  2506 ′. This can be accomplished by configuring the MMIC  2524 ′ in the eastern position to radiate a first wireless signal having a phase (polarity) opposite to the phase (polarity) of a second wireless signal radiated by the western MMIC  2524 ′. 
     These wireless signals combine via superposition of their respective electric fields to form an electromagnetic wave having a TM11 wave mode (horizontally polarized) bound to the dielectric materials  2544 ′ and  2544  with the electric field structures shown in the longitudinal and transverse cross-sectional views shown in  FIG. 25C  (but with a horizontal polarization). Since the TM11 wave mode with horizontal and vertical polarizations are orthogonal (i.e., a dot product of corresponding electric field vectors between any pair of these wave modes at each point of space and time produces a summation of zero), the waveguide device  2522  can be configured to launch these wave modes simultaneously without interference, thereby enabling wave mode division multiplexing. It is further noted that the TM01 wave mode is also orthogonal to the TM11 and TM21 wave modes. 
     While the electromagnetic wave  2502 ′ or  2504 ′ having the TM11 wave mode propagates within the confines of the inner surfaces  2523  of the waveguide device  2522  in regions  2506 ′,  2506 ″,  2508  and  2510 , the TM11 wave mode remains unaltered. However, when the electromagnetic wave  2504 ′ having the TM11 wave mode exits the waveguide device  2522  in region  2512  the inner wall  2523  is no longer present and the TM11 wave mode becomes a hybrid wave mode, specifically, an EH11 wave mode (vertically polarized, horizontally polarized, or both if two electromagnetic waves are launched in region  2506 ′). 
     In yet other embodiments, the waveguide device  2522  can also be configured to launch a TM21 wave mode in region  2506 ′. This can be accomplished by configuring the MMIC  2524 ′ in the northern position to radiate from a signal source a first wireless signal having a phase (polarity) that is in phase (polarity) to a second wireless signal generated from the same signal source by the southern MMIC  2524 ′. At the same time, the MMIC  2524 ′ in the western position is configured to radiate from the same signal source a third wireless signal that is in phase with a fourth wireless signal radiated from the same signal source by the MMIC  2524 ′ located in the eastern position. The north and south MMICs  2524 ′, however, generate first and second wireless signals of opposite polarity to the polarity of the third and fourth wireless signals generated by the western and eastern MMICs  2524 ′. The four wireless signals of alternating polarity combine via superposition of their respective electric fields to form an electromagnetic wave having a TM21 wave mode bound to the dielectric materials  2544 ′ and  2544  with the electric field structures shown in the longitudinal and transverse cross-sectional views shown in  FIG. 25D . When the electromagnetic wave  2504 ′ exits the waveguide device  2522  it may be transformed to a hybrid wave mode such as, for example, an HE21 wave mode, an EH21 wave mode, or a hybrid wave mode with a different radial mode (e.g., HE2m or EH2m, where m&gt;1). 
       FIGS. 25A-25D  illustrate several embodiments for launching TM01, EH11, and other hybrid wave modes utilizing the waveguide device  2522  of  FIG. 25A . With an understanding of the electric field structures of other wave modes that propagate on a coaxial cable (e.g., TM12, TM22, and so on), the MMICs  2524 ′ can be further configured in other ways to launch other wave modes (e.g., EH12, HE22, etc.) that have a low intensity z-field component and phi-field component in the electric field structures near the outer surface of a transmission medium  2542 , which is useful for mitigating propagation losses due to a substance such as water, droplets or other substances that can cause an attenuation of the electric fields of an electromagnetic wave propagating along the outer surface of the transmission medium  2542 . 
       FIG. 26  illustrates a flow diagram of an example, non-limiting embodiment of a method  2560  for sending and receiving electromagnetic waves. Method  2560  can be applied to waveguides  2522  of  FIGS. 23A-23C, 24 and 25A  and/or other waveguide systems or launchers described and shown in the figures of the subject disclosure (e.g.,  FIGS. 7-14, 18D-18K, 22A-22B  and other drawings) for purposes of launching or receiving substantially orthogonal wave modes such as those shown in  FIG. 27 .  FIG. 27  depicts three cross-sectional views of an insulated conductor where a TM00 fundamental wave mode, an HE wave mode with horizontal polarization, and an HE wave mode with vertical polarization, propagates respectively. The electric field structure shown in  FIG. 27  can vary over time and is therefore an illustrative representation at a certain instance or snapshot in time. The wave modes shown in  FIG. 27  are orthogonal to each other. That is, a dot product of corresponding electric field vectors between any pair of the wave modes at each point of space and time produces a summation of zero. This property enables the TM00 wave mode, the HE wave mode with horizontal polarization, and the HE wave mode with vertical polarization to propagate simultaneously along a surface of the same transmission medium in the same frequency band without signal interference. 
     With this in mind, method  2560  can begin at step  2562  where a waveguide system of the subject disclosure can be adapted to receive communication signals from a source (e.g., a base station, a wireless signal transmitted by a mobile or stationary device to an antenna of the waveguide system as described in the subject disclosure, or by way of another communication source.). The communication signals can be, for example, communication signals modulated according to a specific signaling protocol (e.g., LTE, 5G, DOCSIS, DSL, etc.) operating in a native frequency band (e.g., 900 MHz, 1.9 GHz, 2.4 GHz, 5 GHz, etc.), baseband signals, analog signals, other signals, or any combinations thereof. At step  2564 , the waveguide system can be adapted to generate or launch on a transmission medium a plurality of electromagnetic waves according to the communication signals by up-converting (or in some instances down-converting) such communication signals to one or more operating frequencies of the plurality of electromagnetic waves. The transmission medium can be an insulated conductor as shown in  FIG. 28 , or an uninsulated conductor that is subject to environmental exposure to oxidation (or other chemical reaction based on environmental exposure) as shown in  FIGS. 29 and 30 . In other embodiments, the transmission medium can be a dielectric material such as a dielectric core described in  FIG. 18A . 
     To avoid interference, the waveguide system can be adapted to simultaneously launch at step  2564  a first electromagnetic wave using a TM00 wave mode, a second electromagnetic wave using an HE11 wave mode with horizontal polarization, and a third electromagnetic wave using an HE11 wave mode with vertical polarization—see  FIG. 27 . Since the first, second and third electromagnetic waves are orthogonal (i.e., non-interfering) they can be launched in the same frequency band without interference or with a small amount of acceptable interference. The combined transmission of three orthogonal electromagnetic wave modes in the same frequency band constitutes a form of wave mode division multiplexing, which provides a means for increasing the information bandwidth by a factor of three. By combining the principles of frequency division multiplexing with wave mode division multiplexing, bandwidth can be further increased by configuring the waveguide system to launch a fourth electromagnetic wave using a TM00 wave mode, a fifth electromagnetic wave using an HE11 wave mode with horizontal polarization, and a sixth electromagnetic wave using an HE11 wave mode with vertical polarization in a second frequency band that does not overlap with the first frequency band of the first, second and third orthogonal electromagnetic waves. It will be appreciated that other types of multiplexing could be additionally or alternatively used with wave mode division multiplexing without departing from example embodiments. 
     To illustrate this point, suppose each of three orthogonal electromagnetic waves in a first frequency band supports 1 GHz of transmission bandwidth. And further suppose each of three orthogonal electromagnetic waves in a second frequency band also supports 1 GHz of transmission bandwidth. With three wave modes operating in two frequency bands, 6 GHz of information bandwidth is possible for conveying communication signals by way of electromagnetic surface waves utilizing these wave modes. With more frequency bands, the bandwidth can be increased further. 
     Now suppose a transmission medium in the form of an insulated conductor (see  FIG. 28 ) is used for surface wave transmissions. Further suppose the transmission medium has a dielectric layer with thickness proportional to the conductor radius (e.g., a conductor having a 4 mm radius and an insulation layer with a 4 mm thickness). With this type of transmission medium, the waveguide system can be configured to select from several options for transmitting electromagnetic waves. For example, the waveguide system can be configured at step  2564  to transmit first through third electromagnetic waves using wave mode division multiplexing at a first frequency band (e.g., at 1 GHz), third through fourth electromagnetic waves using wave mode division multiplexing at a second frequency band (e.g., at 2.1 GHz), seventh through ninth electromagnetic waves using wave mode division multiplexing at a third frequency band (e.g., at 3.2 GHz), and so on. Assuming each electromagnetic wave supports 1 GHz of bandwidth, collectively the first through ninth electromagnetic waves can support 9 GHz of bandwidth. 
     Alternatively, or contemporaneous with transmitting electromagnetic waves with orthogonal wave modes at step  2564 , the waveguide system can be configured at step  2564  to transmit on the insulated conductor one or more high frequency electromagnetic waves (e.g., millimeter waves). In one embodiment, the one or more high frequency electromagnetic waves can be configured in non-overlapping frequencies bands according to one or more corresponding wave modes that are less susceptible to a water film such as a TM0m wave mode and EH1m wave mode (where m&gt;0), or an HE2m wave mode (where m&gt;1) as previously described. In other embodiments, the waveguide system can instead be configured to transmit one or more high frequency electromagnetic waves in non-overlapping frequency bands according to one or more corresponding wave modes that have longitudinal and/or azimuthal fields near the surface of the transmission medium that may be susceptible to water, but nonetheless exhibit low propagation losses when the transmission medium is dry. A waveguide system can thus be configured to transmit several combinations of wave modes on an insulated conductor (as well as a dielectric-only transmission medium such as a dielectric core) when the insulated conductor is dry. 
     Now suppose a transmission medium in the form of an uninsulated conductor (see  FIGS. 29-30 ) is used for surface wave transmissions. Further consider that the uninsulated conductor or bare conductor is exposed to an environment subject to various levels of moisture and/or rain (as well as air and atmospheric gases like oxygen). Uninsulated conductors, such as overhead power lines and other uninsulated wires, are often made of aluminum which is sometimes reinforced with steel. Aluminum can react spontaneously with water and/or air to form aluminum oxide. An aluminum oxide layer can be thin (e.g., nano to micrometers in thickness). An aluminum oxide layer has dielectric properties and can therefore serve as a dielectric layer. Accordingly, uninsulated conductors can propagate not only TM00 wave modes, but also other wave modes such as an HE wave mode with horizontal polarization, and an HE wave mode with vertical polarization at high frequencies based at least in part on the thickness of the oxide layer. Accordingly, uninsulated conductors having an environmentally formed dielectric layer such as an oxide layer can be used for transmitting electromagnetic waves using wave mode division multiplexing and frequency division multiplexing. Other electromagnetic waves having a wave mode (with or without a cutoff frequency) that can propagate on an oxide layer are contemplated by the subject disclosure and can be applied to the embodiments described in the subject disclosure. 
     In one embodiment, the term “environmentally formed dielectric layer” can represent an uninsulated conductor that is exposed to an environment that is not artificially created in a laboratory or other controlled setting (e.g., bare conductor exposed to air, humidity, rain, etc. on a utility pole or other exposed environment). In other embodiments, an environmentally formed dielectric layer can be formed in a controlled setting such as a manufacturing facility that exposes uninsulated conductors to a controlled environment (e.g., controlled humidity, or other gaseous substance) that forms a dielectric layer on the outer surface of the uninsulated conductor. In yet another alternative embodiment, the uninsulated conductor can also be “doped” with particular substances/compounds (e.g., a reactant) that facilitate chemical reactions with other substances/compounds that are either available in a natural environment or in an artificially created laboratory or controlled setting, thereby resulting in the creation of the environmentally formed dielectric layer. 
     Wave mode division multiplexing and frequency division multiplexing can prove useful in mitigating obstructions such as water accumulating on an outer surface of a transmission medium. To determine if mitigating an obstruction is necessary, a waveguide system can be configured at step  2566  to determine if an obstruction is present on the transmission medium. A film of water (or water droplets) collected on an outer surface of the transmission medium due to rain, condensation, and/or excess humidity can be one form of an obstruction that can cause propagation losses in electromagnetic waves if not mitigated. A splicing of a transmission medium or other object coupled to the outer surface of the transmission medium can also serve as an obstruction. 
     Obstructions can be detected by a source waveguide system that transmits electromagnetic waves on a transmission medium and measures reflected electromagnetic waves based on these transmissions. Alternatively, or in combination, the source waveguide system can detect obstructions by receiving communication signals (wireless or electromagnetic waves) from a recipient waveguide system that receives and performs quality metrics on electromagnetic waves transmitted by the source waveguide system. When an obstruction is detected at step  2566 , the waveguide system can be configured to identify options to update, modify, or otherwise change the electromagnetic waves being transmitted. 
     Suppose, for example, that in the case of an insulated conductor, the waveguide system had launched at step  2564  a high order wave mode such as TM01 wave mode with a frequency band that starts at 30 GHz having a large bandwidth (e.g., 10 GHz) when the insulated conductor is dry. For illustration purposes, a 10 GHz bandwidth will be assumed for an electromagnetic wave having a TM01 wave mode. 
     Although it was noted earlier in the subject disclosure that a TM01 wave mode has a desirable electric field alignment that is not longitudinal and not azimuthal near the outer surface, it can nonetheless be subject to some signal attenuation which in turn reduces its operating bandwidth when a water film (or droplets) accumulates on the insulated conductor. An electromagnetic wave having a TM01 wave mode with a bandwidth of approximately 10 GHz (30 to 40 GHz) on a dry insulated conductor can drop to a bandwidth of approximately 1 GHz (30 to 31 GHz) when the insulated conductor is wet. To mitigate the loss in bandwidth, the waveguide system can be configured to launch electromagnetic waves at much lower frequencies (e.g., less than 6 GHz) using wave mode division multiplexing and frequency division multiplexing. 
     For example, the waveguide system can be configured to transmit a first set of electromagnetic waves; specifically, a first electromagnetic wave having a TM00 wave mode, a second electromagnetic wave having an HE11 wave mode with horizontal polarization, and a third electromagnetic wave having an HE11 wave mode with vertical polarization, each electromagnetic wave having a center frequency at 1 GHz. Assuming a useable frequency band from 500 MHz to 1.5 GHz to convey communication signals, each electromagnetic wave can provide 1 GHz of bandwidth, and collectively 3 GHz of system bandwidth. 
     Suppose also the waveguide system is configured to transmit a second set of electromagnetic waves; specifically, a fourth electromagnetic wave having a TM00 wave mode, a fifth electromagnetic wave having an HE11 wave mode with horizontal polarization, and a sixth electromagnetic wave having an HE11 wave mode with vertical polarization, each electromagnetic wave having a center frequency at 2.1 GHz. Assuming a frequency band from 1.6 GHz to 2.6 GHz, with a guard band of 100 MHz between the first and second sets of electromagnetic waves, each electromagnetic wave can provide 1 GHz of bandwidth, and collectively 3 GHz of additional bandwidth, thereby now providing up to 6 GHz of system bandwidth. 
     Further suppose the waveguide system is also configured to transmit a third set of electromagnetic waves; specifically, a seventh electromagnetic wave having a TM00 wave mode, an eighth electromagnetic wave having an HE wave mode with horizontal polarization, and a ninth electromagnetic wave having an HE wave mode with vertical polarization, each electromagnetic wave having a center frequency at 3.2 GHz. Assuming a frequency band from 2.7 GHz to 3.7 GHz, with a guard band of 100 MHz between the second and third sets of electromagnetic waves, each electromagnetic wave can provide 1 GHz of bandwidth, and collectively 3 GHz of additional bandwidth, thereby now providing up to 9 GHz of system bandwidth. 
     The combination of the TM01 wave mode, and the three sets of electromagnetic waves configured for wave mode division multiplexing and frequency division multiplexing, provide a total system bandwidth of 10 GHz, thereby restoring a bandwidth of 10 GHz previously available when the high frequency electromagnetic wave having the TM01 wave mode was propagating on a dry insulated conductor.  FIG. 31  illustrates a process for performing mitigation of a TM01 wave mode subject to an obstruction such as a water film.  FIG. 31  illustrates a transition from a dry insulated conductor that supports a high bandwidth TM01 wave mode to a wet insulated conductor that supports a lower bandwidth TM01 wave mode that is combined with low frequency TM00 and HE11 wave modes configured according to wave mode division multiplexing (WMDM) and frequency division multiplexing (FDM) schemes to restore losses in system bandwidth. 
     Consider now an uninsulated conductor where the waveguide system had launched at step  2564  a TM00 wave mode with a frequency band that starts at 10 GHz having a large bandwidth (e.g., 10 GHz). Suppose now that transmission medium propagating the 10 GHz TM00 wave mode is exposed to an obstruction such as water. As noted earlier, a high frequency TM00 wave mode on an insulated conductor is subject to a substantial amount of signal attenuation (e.g., 45 dB/M at 10 GHz) when a water film (or droplets) accumulates on the outer surface of the insulated conductor. Similar attenuations will be present for a 10 GHz (or greater) TM00 wave mode propagating on an “uninsulated” conductor. An environmentally exposed uninsulated conductor (e.g., aluminum), however, can have an oxide layer formed on the outer surface which can serve as a dielectric layer that supports wave modes other than TM00 (e.g., HE11 wave modes). It is further noted that at lower frequencies a TM00 wave mode propagating on an insulated conductor exhibits a much lower attenuation (e.g., 0.62 dB/M at 4 GHz). A TM00 wave mode operating at less than 6 GHz would similarly exhibit low propagation losses on an uninsulated conductor. Accordingly, to mitigate the loss in bandwidth, the waveguide system can be configured to launch electromagnetic waves having a TM00 wave mode at lower frequencies (e.g., 6 GHz or less) and electromagnetic waves having an HE11 wave mode configured for WMDM and FDM at higher frequencies. 
     Referring back to  FIG. 26 , suppose then that the waveguide system detects an obstruction such as water at step  2566  on an environmentally exposed uninsulated conductor. A waveguide system can be configured to mitigate the obstruction by transmitting a first electromagnetic wave configured with a TM00 wave mode having a center frequency at 2.75 GHz. Assuming a useable frequency band from 500 MHz to 5.5 GHz to convey communication signals, the electromagnetic waves can provide 5 GHz of system bandwidth. 
       FIG. 32  illustrates a process for performing mitigation of a high frequency TM00 wave mode subject to an obstruction such as a water film detected at step  2566 .  FIG. 31  illustrates a transition from a dry uninsulated conductor that supports a high bandwidth TM00 wave mode to a wet uninsulated conductor that combines a low frequency TM00 wave mode and high frequency HE11 wave modes configured according to WMDM and FDM schemes to restore losses in system bandwidth. 
     It will be appreciated that the aforementioned mitigation techniques are non-limiting. For example, the center frequencies described above can differ between systems. Additionally, the original wave mode used before an obstruction is detected can differ from the illustrations above. For example, in the case of an insulated conductor an EH11 wave mode can be used singly or in combination with a TM01 wave mode. It is also appreciated that WMDM and FDM techniques can be used to transmit electromagnetic waves at all times and not just when an obstruction is detected at step  2566 . It is further appreciated that other wave modes that can support WMDM and/or FDM techniques can be applied to and/or combined with the embodiments described in the subject disclosure, and are therefore contemplated by the subject disclosure. 
     Referring back to  FIG. 26 , once a mitigation scheme using WMDM and/or FDM has been determined in accordance with the above illustrations, the waveguide system can be configured at step  2568  to notify one or more other waveguide systems of the mitigation scheme intended to be used for updating one or more electromagnetic waves prior to executing the update at step  2570 . The notification can be sent wirelessly to one or more other waveguide systems utilizing antennas if signal degradation in the electromagnetic waves is too severe. If signal attenuation is tolerable, then the notification can be sent via the affected electromagnetic waves. In other embodiments, the waveguide system can be configured to skip step  2568  and perform the mitigation scheme using WMDM and/or FDM at step  2570  without notification. This embodiment can be applied in cases where, for example, other recipient waveguide system(s) know beforehand what kind of mitigation scheme would be used, or the recipient waveguide system(s) are configured to use signal detection techniques to discover the mitigation scheme. Once the mitigation scheme using WMDM and/or FDM has been initiated at step  2570 , the waveguide system can continue to process received communication signals at steps  2562  and  2564  as described earlier using the updated configuration of the electromagnetic waves. 
     At step  2566 , the waveguide system can monitor if the obstruction is still present. This determination can be performed by sending test signals (e.g., electromagnetic surface waves in the original wave mode) to other waveguide system(s) and awaiting test results back from the waveguide systems if the situation has improved, and/or by using other obstruction detection techniques such as signal reflection testing based on the sent test signals. Once the obstruction is determined to have been removed (e.g., the transmission medium becomes dry), the waveguide system can proceed to step  2572  and determine that a signal update was performed at step  2568  using WMDM and/or FDM as a mitigation technique. The waveguide system can then be configured to notify recipient waveguide system(s) at step  2568  of the intent to restore transmissions to the original wave mode, or bypass this step and proceed to step  2570  where it restores transmissions to an original wave mode and assumes the recipient waveguide system(s) know the original wave modes and corresponding transmission parameters, or can otherwise detect this change. 
     A waveguide system can also be adapted to receive electromagnetic waves configured for WMDM and/or FDM. For example, suppose that an electromagnetic wave having a high bandwidth (e.g., 10 GHz) TM01 wave mode is propagating on an insulated conductor as shown in  FIG. 31  and that the electromagnetic wave is generated by a source waveguide system. At step  2582 , a recipient waveguide system can be configured to process the single electromagnetic wave with the TM01 wave mode under normal condition. Suppose, however, that the source waveguide system transitions to transmitting electromagnetic waves using WMDM and FDM along with a TM01 wave mode with a lower bandwidth on the insulated conductor, as previously described in  FIG. 31 . In this instance, the recipient waveguide system would have to process multiple electromagnetic waves of different wave modes. Specifically, the recipient waveguide system would be configured at step  2582  to selectively process each of the first through ninth electromagnetic waves using WMDM and FDM and the electromagnetic wave using the TM01 wave mode as shown in  FIG. 31 . 
     Once the one or more electromagnetic waves have been received at step  2582 , the recipient waveguide can be configured to use signal processing techniques to obtain the communication signals that were conveyed by the electromagnetic wave(s) generated by the source waveguide system at step  2564  (and/or step  2570  if an update has occurred). At step  2586 , the recipient waveguide system can also determine if the source waveguide system has updated the transmission scheme. The update can be detected from data provided in the electromagnetic waves transmitted by the source waveguide system, or from wireless signals transmitted by the source waveguide system. If there are no updates, the recipient waveguide system can continue to receive and process electromagnetic waves at steps  2582  and  2584  as described before. If, however, an update is detected at step  2586 , the recipient waveguide system can proceed to step  2588  to coordinate the update with the source waveguide system and thereafter receive and process updated electromagnetic waves at steps  2582  and  2584  as described before. 
     It will be appreciated that method  2560  can be used in any communication scheme including simplex and duplex communications between waveguide systems. Accordingly, a source waveguide system that performs an update for transmitting electromagnetic waves according to other wave modes will in turn cause a recipient waveguide system to perform similar steps for return electromagnetic wave transmissions. It will also be appreciated that the aforementioned embodiments associated with method  2560  of  FIG. 26  and the embodiments shown in  FIGS. 27 through 32  can be combined in whole or in part with other embodiments of the subject disclosure for purposes of mitigating propagation losses caused by an obstruction at or in a vicinity of an outer surface of a transmission medium (e.g., insulated conductor, uninsulated conductor, or any transmission medium having an external dielectric layer). The obstruction can be a liquid (e.g., water), a solid object disposed on the outer surface of the transmission medium (e.g., ice, snow, a splice, a tree limb, etc.), or any other objects located at or near the outer surface of the transmission medium. 
     While for purposes of simplicity of explanation, the respective processes are shown and described as a series of blocks in  FIG. 26 , it is to be understood and appreciated that the claimed subject matter is not limited by the order of the blocks, as some blocks may occur in different orders and/or concurrently with other blocks from what is depicted and described herein. Moreover, not all illustrated blocks may be required to implement the methods described herein. 
     Referring now to  FIGS. 33 and 34 , block diagrams illustrating example, non-limiting embodiments for transmitting orthogonal wave modes according to the method  2560  of  FIG. 26  are shown.  FIG. 33  depicts an embodiment for simultaneously transmitting a TM00 wave mode, an HE11 wave mode with vertical polarization, and an HE11 wave mode with horizontal polarization as depicted in an instance in time in  FIG. 27 . In one embodiment, these orthogonal wave modes can be transmitted with a waveguide launcher having eight (8) MMICs as shown in  FIG. 18K  located at symmetrical locations (e.g., north, northeast, east, southeast, south, southwest, west, and northwest). The waveguide launcher of FIG. (or  FIG. 18J ) can also be configured with these 8 MMICs. Additionally, the waveguide launcher can be configured with a cylindrical sleeve  2523 A and tapered dielectric that wraps around the transmission medium (e.g., insulated conductor, uninsulated conductor, or other cable with a dielectric layer such as dielectric core). The housing assembly of the waveguide launcher (not shown) can be configured to include a mechanism (e.g., a hinge) to enable a longitudinal opening of the waveguide launcher for placement and latching around a circumference of a transmission medium. 
     With these configurations in mind, the waveguide launcher can include three transmitters (TX 1 , TX 2 , and TX 3 ) coupled to MMICs having various coordinate positions (see  FIG. 25AG  and  FIG. 18W ). The interconnectivity between the transmitters (TX 1 , TX 2 , and TX 3 ) and the MMICs can be implemented with a common printed circuit board or other suitable interconnecting technology. The first transmitter (TX 1 ) can be configured to launch a TM00 wave mode, the second transmitter (TX 2 ) can be configured to launch an HE11 vertical polarization wave mode, and the third transmitter (TX 3 ) can be configured to launch an HE11 horizontal polarization wave mode. 
     A first signal port (shown as “SP 1 ”) of the first transmitter (TX 1 ) can be coupled in parallel to each of the 8 MMICs. A second signal port (shown as “SP 2 ”) of the first transmitter (TX 1 ) can be coupled to a conductive sleeve  2523 A that is placed on the transmission medium by the waveguide launcher as noted above. The first transmitter (TX 1 ) can be configured to receive a first group of the communication signals described in step  2562  of  FIG. 26 . The first group of communication signals can be frequency-shifted by the first transmitter (TX 1 ) from their native frequencies (if necessary) for an orderly placement of the communication signals in channels of a first electromagnetic wave configured according to the TM00 wave mode. The 8 MMICs coupled to the first transmitter (TX 1 ) can be configured to up-convert (or down-convert) the first group of the communication signals to the same center frequency (e.g., 1 GHz for the first electromagnetic wave as described in relation to  FIG. 31 ). All 8 MMICs would have synchronized reference oscillators that can be phase locked using various synchronization techniques. 
     Since the 8 MMICs receive signals from the first signal port of the first transmitter (TX 1 ) based on the reference provided by the second signal port, the 8 MMICs thereby receive signals with the same polarity. Consequently, once these signals have been up-converted (or down-converted) and processed for transmission by the 8 MMICs, one or more antennas of each of the 8 MMICs simultaneously radiates signals with electric fields of the same polarity. Collectively, MMICs that are opposite in location to each other (e.g., MMIC north and MMIC south) will have an electric field structure aligned towards or away from the transmission medium, thereby creating at a certain instance in time an outward field structure like the TM00 wave mode shown in  FIG. 27 . Due to the constant oscillatory nature of the signals radiated by the 8 MMICs, it will be appreciated that at other instances in time, the field structure shown in  FIG. 27  will radiate inward. By symmetrically radiating electric fields with the same polarity the collection of opposing MMICs contribute to the inducement of a first electromagnetic wave having a TM00 wave mode that propagates on a transmission medium with a dielectric layer and can convey the first group of the communication signals to a receiving waveguide system. 
     Turning now to the second transmitter (TX 2 ) in  FIG. 33 , this transmitter has a first signal port (SP 1 ) coupled to MMICs located in north, northeast and northwest positions, while a second signal port (SP 2 ) of the second transmitter (TX 2 ) is coupled to the MMICs located in south, southeast and southwest positions (see  FIG. 18K ). The second transmitter (TX 2 ) can be configured to receive a second group of the communication signals described in step  2562  of  FIG. 26 , which differs from the first group of the communication signals received by the first transmitter (TX 1 ). The second group of communication signals can be frequency-shifted by the second transmitter (TX 2 ) from their native frequencies (if necessary) for an orderly placement of the communication signals in channels of a second electromagnetic wave configured according to an HE11 wave mode with vertical polarization. The 6 MMICs coupled to the second transmitter (TX 2 ) can be configured to up-convert (or down-conversion) the second group of the communication signals to the same center frequency as used for the TM00 wave mode (i.e., 1 GHz as described in relation to  FIG. 31 ). Since a TM00 wave mode is orthogonal to an HE11 wave mode with vertical polarization, they can share the same center frequency in an overlapping frequency band without interference. 
     Referring back to  FIG. 33 , the first signal port (SP 1 ) of the second transmitter (TX 2 ) generates signals of opposite polarity to the signals of the second signal port (SP 2 ). As a result, the electric field alignment of signals generated by one or more antennas of the northern MMIC will be of opposite polarity to the electric field alignment of signals generated by one or more antennas of the southern MMIC. Consequently, the electric fields of the north and south MMICs will have an electric field structure that is vertically aligned in the same direction, thereby creating at a certain instance in time a northern field structure like the HE11 wave mode with vertical polarization shown in  FIG. 27 . Due to the constant oscillatory nature of the signals radiated by the north and south MMICs, it will be appreciated that at other instances in time, the HE11 wave mode will have a southern field structure. Similarly, based on the opposite polarity of signals supplied to the northeast and southeast MMICs by the first and second signal ports, respectively, these MMICs will generate at a certain instance in time the curved electric field structure shown on the east side of the HE11 wave mode with vertical polarization depicted in  FIG. 27 . Also, based on the opposite polarity of signals supplied to the northwest and southwest MMICs, these MMICs will generate at a certain instance in time the curved electric field structure shown on the west side of the HE11 wave mode with vertical polarization depicted in  FIG. 27 . 
     By radiating electric fields with opposite polarity by opposing MMICs (north, northeast and northwest versus south, southeast and southwest), the collection of signals with a directionally aligned field structure contribute to the inducement of a second electromagnetic wave having the HE11 wave mode with vertical polarization shown in  FIG. 27 . The second electromagnetic wave propagates along the “same” transmission medium as previously described for the first transmitter (TX 1 ). Given the orthogonality of a TM00 wave mode and an HE11 wave mode with vertical polarization, there will be ideally no interference between the first electromagnetic wave and the second electromagnetic wave. Consequently, the first and second electromagnetic waves having overlapping frequency bands propagating along the same transmission medium can successfully convey the first and second groups of the communication signals to the same (or other) receiving waveguide system. 
     Turning now to the third transmitter (TX 3 ) in  FIG. 33 , this transmitter has a first signal port (SP 1 ) coupled to MMICs located in east, northeast and southeast positions, while a second signal port (SP 2 ) of the third transmitter (TX 3 ) is coupled to the MMICs located in west, northwest and southwest positions (see  FIG. 18K ). The third transmitter (TX 3 ) can be configured to receive a third group of the communication signals described in step  2562  of  FIG. 26 , which differs from the first and second groups of the communication signals received by the first transmitter (TX 1 ) and the second transmitter (TX 2 ), respectively. The third group of communication signals can be frequency-shifted by the third transmitter (TX 3 ) from their native frequencies (if necessary) for an orderly placement of the communication signals in channels of a second electromagnetic wave configured according to an HE11 wave mode with horizontal polarization. The 6 MMICs coupled to the third transmitter (TX 3 ) can be configured to up-convert (or down-conversion) the third group of the communication signals to the same center frequency as used for the TM00 wave mode and HE11 wave mode with vertical polarization (i.e., 1 GHz as described in relation to  FIG. 31 ). Since a TM00 wave mode, an HE11 wave mode with vertical polarization, and an HE11 wave mode with horizontal polarization are orthogonal, they can share the same center frequency in an overlapping frequency band without interference. 
     Referring back to  FIG. 33 , the first signal port (SP 1 ) of the third transmitter (TX 3 ) generates signals of opposite polarity to the signals of the second signal port (SP 2 ). As a result, the electric field alignment of signals generated by one or more antennas of the eastern MMIC will be of opposite polarity to the electric field alignment of signals generated by one or more antennas of the western MMIC. Consequently, the electric fields of the east and west MMICs will have an electric field structure that is horizontally aligned in the same direction, thereby creating at a certain instance in time a western field structure like the HE11 wave mode with horizontal polarization shown in  FIG. 27 . Due to the constant oscillatory nature of the signals radiated by the east and west MMICs, it will be appreciated that at other instances in time, the HE wave mode will have an eastern field structure. Similarly, based on the opposite polarity of signals supplied to the northeast and northwest MMICs by the first and second signal ports, respectively, these MMICs will generate at a certain instance in time the curved electric field structure shown on the north side of the HE11 wave mode with horizontal polarization depicted in  FIG. 27 . Also, based on the opposite polarity of signals supplied to the southeast and southwest MMICs, these MMICs will generate at a certain instance in time the curved electric field structure shown on the south side of the HE11 wave mode with horizontal polarization depicted in  FIG. 27 . 
     By radiating electric fields with opposite polarity by opposing MMICs (east, northeast and southeast versus west, northwest and southwest), the collection of signals with a directionally aligned field structure contribute to the inducement of a third electromagnetic wave having the HE wave mode with horizontal polarization shown in  FIG. 27 . The third electromagnetic wave propagates along the “same” transmission medium as previously described for the first transmitter (TX 1 ) and the second transmitter (TX 2 ). Given the orthogonality of a TM00 wave mode, an HE11 wave mode with vertical polarization, and an HE wave mode with horizontal polarization, there will be, ideally, no interference between the first electromagnetic wave, the second electromagnetic wave, and the third electromagnetic wave. Consequently, the first, second and third electromagnetic waves having overlapping frequency bands propagating along the same transmission medium can successfully convey the first, second and third groups of the communication signal to the same (or other) receiving waveguide system. 
     Because of the orthogonality of the electromagnetic waves described above, a recipient waveguide system can be configured to selectively retrieve the first electromagnetic wave having the TM00 wave mode, the second electromagnetic wave having the HE11 wave mode with vertical polarization, and the third electromagnetic wave having the HE11 wave mode with horizontal polarization. After processing each of these electromagnetic waves, the recipient waveguide system can be further configured to obtain the first, second and third group of the communication signals conveyed by these waves.  FIG. 34  illustrates a block diagram for selectively receiving each of the first, second and third electromagnetic waves. 
     Specifically, the first electromagnetic wave having the TM00 wave mode can be selectively received by a first receiver (RX 1 ) shown in  FIG. 34  by taking the difference between the signals received by all 8 MMICs and the signal reference provided by the metal sleeve  2523 A as depicted in the block diagram in  FIG. 35 . The second electromagnetic wave having the HE11 wave mode with vertical polarization can be selectively received by a second receiver (RX 2 ) shown in  FIG. 34  by taking the difference between the signals received by the MMICs located in north, northeast and northwest positions and the signals received by the MMICs located in south, southeast and southwest positions as depicted in the block diagram in  FIG. 36 . The third electromagnetic wave having the HE11 wave mode with horizontal polarization can be selectively received by a third receiver (RX 3 ) shown in  FIG. 34  by taking the difference between the signals received by the MMICs located in east, northeast and southeast positions and the signals received by the MMICs located in west, northwest and southwest positions as depicted in the block diagram in  FIG. 37 . 
       FIG. 38  illustrates a simplified functional block diagram of an MMIC. The MMIC can, for example, utilize a mixer coupled to a reference (TX) oscillator that shifts one of the communication signals supplied by one of the signal ports (SP 1  or SP 2 ) of one of the transmitters (TX 1 , TX 2  or TX 3 ) to a desired center frequency in accordance with the configurations shown in  FIG. 33 . For example, in the case of TX  1 , the communication signal from SP 1  is supplied to a transmit path of each of the MMICs (i.e., NE, NW, SE, SW, N, S, E, and W). In the case of TX 2 , the communication signal from SP 1  is supplied to another transmit path of three MMICs (i.e., N, E, and NW). Note the transmit paths used by MMICs N, E and W for the communication signal supplied by SP 1  of TX 2  are different from the transmit paths used by the MMICs for the communication signal supplied by SP 1  of TX 1 . Similarly, the communication signal from SP 2  of TX 2  is supplied to another transmit path of three other MMICs (i.e., S, SE, and SW). Again, the transmit paths used by MMICs S, SE and SW for the communication signal supplied by SP 2  of TX 2  are different from the transmit paths used by the MMICs for the communication signals from SP 1  of TX 1 , and SP 1  of TX 2 . Lastly, in the case of TX 3 , the communication signal from SP 1  is supplied to yet another transmit path of three MMICs (i.e., E, NE, and SE). Note the transmit paths used for MMICs E, NE, and SE for the communication signal from SP 1  of TX 3  are different from the transmit paths used by the MMICs for the communication signals supplied by SP 1  of TX 1 , SP 1  of TX 2 , and SP 2  of TX 2 . Similarly, the communication signal from SP 2  of TX 3  is supplied to another transmit path of three other MMICs (i.e., W, NW, and SW). Again, the transmit paths used by MMICs W, NW, and SW for the communication signal supplied by SP 2  of TX 3  are different from the transmit paths used by the MMICs for the communication signals from SP 1  of TX 1 , SP 1  of TX 2 , and SP 2  of TX 2 , and SP 1  of TX 3 . 
     Once the communication signals have been frequency-shifted by the mixer shown in the transmit path, the frequency-shifted signal generated by the mixer can then be filtered by a bandpass filter that removes spurious signals. The output of the bandpass filter in turn can be provided to a power amplifier that couples to an antenna by way of a duplexer for radiating signals in the manner previously described. The duplexer can be used to isolate a transmit path from a receive path. The illustration of  FIG. 38  is intentionally oversimplified to enable ease of illustration. 
     It will be appreciated that other components (not shown) such as an impedance matching circuit, phase lock loop, or other suitable components for improving the accuracy and efficiency of the transmission path (and receive path) is contemplated by the subject disclosure. Furthermore, while a single antenna can be implemented by each MMIC, other designs with multiple antennas can likewise be employed. It is further appreciated that to achieve more than one orthogonal wave mode with overlapping frequency bands (e.g., TM00, HE11 Vertical, and HE11 Horizontal wave modes described above), the transmit path can be repeated N times using the same reference oscillator. N can represent an integer associated with the number of instances the MMIC is used to generate each of the wave modes. For example, in  FIG. 33 , MMIC NE is used three times; hence, MMIC NE has three transmit paths (N=3), MMIC NW is used three times; hence, MMIC NW has three transmit paths (N=3), MMIC N is used twice; hence, MMIC N has two transmit paths (N=2), and so on. If frequency division multiplexing is employed to generate the same wave modes in other frequency band(s) (see  FIGS. 31 and 32 ), the transmit path can be further repeated using different reference oscillator(s) that are centered at the other frequency band(s). 
     In the receive path shown in  FIG. 38 , N signals supplied by N antennas via the duplexer of each transmit path in the MMIC can be filtered by a corresponding N bandpass filters, which supply their output to N low-noise amplifiers. The N low-noise amplifiers in turn supply their signals to N mixers to generate N intermediate-frequency received signals. As before, N is representative of the number of instances the MMIC is used for receiving wireless signals for different wave modes. For example, in  FIG. 34 , MMIC NE is used in three instances; hence, MMIC NE has three receive paths (N=3), MMIC N is used in two instances; hence, MMIC N has two receive paths (N=2), and so on. 
     Referring back to  FIG. 38 , to reconstruct a wave mode signal, Y received signals supplied by receiver paths of certain MMICs or a reference from a metal sleeve is subtracted from X received signals supplied by other MMICs based on the configurations shown in  FIGS. 35-37 . For example, a TM00 signal is reconstructed by supplying the received signals of all MMICs (NE, NW, SE, SW, N, S, E, W) to the plus port of the summer (i.e., X signals), while the reference signal from the metal sleeve is supplied to the negative port of the summer (i.e., Y signal)—see  FIG. 35 . The difference between the X and Y signals results in the TM00 signal. To reconstruct the HE11 Vertical signal, the received signals of MMICs N, NE, and NW are supplied to the plus port of the summer (i.e., X signals), while the received signals of MMICs S, SE, and SW are supplied to the negative port of the summer (i.e., Y signals)—see  FIG. 36 . The difference between the X and Y signals results in the HE11 vertical signal. Lastly, to reconstruct the HE11 Horizontal signal, the received signals of MMICs E, NE, and SE are supplied to the plus port of the summer (i.e., X signals), while the received signals of MMICs W, NW, and SW are supplied to the negative port of the summer (i.e., Y signals)—see  FIG. 37 . The difference between the X and Y signals results in the HE11 horizontal signal. Since there are three wave mode signals being reconstructed, the block diagram of the summer with the X and Y signals is repeated three times. 
     Each of these reconstructed signals is at intermediate frequencies. These intermediate-frequency signals are provided to receivers (RX 1 , RX 2  and RX 3 ) which include circuitry (e.g., a DSP, A/D converter, etc.) for processing and to selectively obtain communication signals therefrom. Similar to the transmit paths, the reference oscillators of the three receiver paths can be configured to be synchronized with phase lock loop technology or other suitable synchronization technique. If frequency division multiplexing is employed for the same wave modes in other frequency band(s) (see  FIGS. 31 and 32 ), the receiver paths can be further repeated using a different reference oscillator that is centered at the other frequency band(s). 
     It will be appreciated that other suitable designs that can serve as alternative embodiments to those shown in  FIGS. 33-38  can be used for transmitting and receiving orthogonal wave modes. For example, there can be fewer or more MMICs than described above. In place of the MMICs, or in combination, slotted launchers as shown in  FIGS. 18D-18E, 18G, and 18I  can be used. It is further appreciated that more or fewer sophisticated functional components can be used for transmitting or receiving orthogonal wave modes. Accordingly, other suitable designs and/or functional components are contemplated by the subject disclosure for transmitting and receiving orthogonal wave modes. 
     Referring now to  FIG. 39 , a block diagram illustrating an example, non-limiting embodiment of a polyrod antenna  2600  for transmitting wireless signals is shown. The polyrod antenna  2600  can be one of a number of polyrod antennas that are utilized in an antenna array, such as array  1976  of  FIG. 19F . The antenna array can facilitate or otherwise enable beam steering which can include beam forming. The beam steering can be associated with communication signals, including voice, video, data, messaging, testing signals. 
     In one or more embodiments, the polyrod antenna  2600  can include a core  2628  having a number of different regions or portions. The core  2628  can be connected with a waveguide  2622  configured to confine an electromagnetic wave at least in part within the core (e.g., in a first region of the core covered by the waveguide). In one embodiment (not shown), the waveguide  2622  can have an opening for accepting a transmission medium (e.g., a dielectric cable) or other coupling devices. In another embodiment, the waveguide  2622  can have a generator, radiating element or other components therein that generate electromagnetic waves for propagating along the core  2628 . 
     In one embodiment, another region  2606  of the core  2628  (e.g., outside of the waveguide  2622 ) is configured to reduce a propagation loss of an electromagnetic wave as the electromagnetic wave propagates into that region, such as by having a non-tapered or otherwise uniform diameter of the core. The particular length and/or diameter of the region  2606  of the core  2628  can be selected to facilitate the reduction of propagation loss of the electromagnetic wave. 
     In one embodiment, another region  2612  of the core  2628  (e.g., the distal portion or end of the core that is outside of the waveguide  2622 ) can be tapered and can facilitate transmitting a wireless signal, such as based on the electromagnetic wave propagating along the core  2628 . The particular length, diameter, and/or angle of taper of the region  2612  of the core  2628  can be selected to facilitate transmitting of the wireless signals. In one embodiment, the tip or end  2675  of the region  2612  can be truncated (as shown in  FIG. 39 ) or pointed. 
     In one embodiment, the length and/or diameter of the core  2628  can be selected based on a wavelength of the electromagnetic wave that will be propagating along the dielectric core. For example, a diameter of greater than ¼λ can be used for the region  2606 . 
     In one embodiment, an inner surface of the waveguide  2622  can be constructed from a metallic material or other materials that reflect electromagnetic waves and thereby enables the waveguide  2622  to be configured to guide the electromagnetic wave towards the core  2628 . In one embodiment, the core  2628  can comprise a dielectric core (e.g., as described herein) that extends to, or in proximity of, the inner surface of the waveguide  2622 . In another embodiment, the dielectric core can be surrounded by cladding (such as shown in  FIG. 18A ), whereby the cladding extends to the inner surface of the waveguide  2622 . In yet other embodiments, the core  2628  can comprise an insulated conductor, where the insulation extends to the inner surface of the waveguide  2622 . In this embodiment, the insulated conductor can be a power line, a coaxial cable, or other types of insulated conductors. In one example, the tapered outer shape may extend to the diameter of the metallic wire. In another example, the tapered outer shape may extend to and include tapering of the metallic wire. In yet another example, the metallic wire may or may not continue beyond the tip  2675 . 
     Referring to  FIG. 40 , an e-field distribution is illustrated for the polyrod antenna  2600 . As shown, the electromagnetic wave is confined or substantially confined within the waveguide  2622  and then propagates along the core  2628  until it is transmitted as a wireless signal from the region  2612  of the core. 
     Referring now to  FIGS. 41 and 42 , diagrams are shown illustrating an example, non-limiting embodiment of a polyrod antenna array  2900  which utilizes four polyrod antennas  2600  for transmitting wireless signals. In this example, the polyrod antenna array  2900  utilizes the same polyrod antennas  2600 , which are uniformly spaced apart, such as 0.8 cm on center. The particular type of polyrod antenna, the number of polyrod antennas, and/or the spacing in the array can be selected according to various factors, such as based on parameters of the wireless signals and/or electromagnetic waves that are being utilized. 
     Referring now to  FIG. 43A , a block diagram illustrating an example, non-limiting embodiment of a hollow horn antenna  3600  is shown. In one embodiment, the hollow horn antenna  3600  can be used in an array. As an example, hollow horn antenna  3600  can be made from Teflon® and/or can include a cylindrical V-band feed  3622  for generating a signal to be wirelessly transmitted.  FIG. 43B  illustrates an e-field distribution for the hollow horn antenna  3600 . As shown, the electromagnetic waves are confined or substantially confined within the cylinder  3622 . 
     Turning now to  FIG. 44A , a block diagram illustrating an example, non-limiting embodiment of a communication system  4400  in accordance with various aspects of the subject disclosure is shown. The communication system  4400  can include a macro base station  4402  such as a base station or access point having antennas that covers one or more sectors (e.g., 6 or more sectors). The macro base station  4402  can be communicatively coupled to a communication node  4404 A that serves as a master or distribution node for other communication nodes  4404 B-E distributed at differing geographic locations inside or beyond a coverage area of the macro base station  4402 . The communication nodes  4404  operate as a distributed antenna system configured to handle communications traffic associated with client devices such as mobile devices (e.g., cell phones) and/or fixed/stationary devices (e.g., a communication device in a residence, or commercial establishment) that are wirelessly coupled to any of the communication nodes  4404 . In particular, the wireless resources of the macro base station  4402  can be made available to mobile devices by allowing and/or redirecting certain mobile and/or stationary devices to utilize the wireless resources of a communication node  4404  in a communication range of the mobile or stationary devices. 
     The communication nodes  4404 A-E can be communicatively coupled to each other over an interface  4410 . In one embodiment, the interface  4410  can comprise a wired or tethered interface (e.g., fiber optic cable). In other embodiments, the interface  4410  can comprise a wireless RF interface forming a radio distributed antenna system. In various embodiments, the communication nodes  4404 A-E can include one or more antennas, such as dielectric horn antennas or antenna arrays, poly rod antennas or antenna arrays or any of the other antennas described herein. The communication nodes  4404 A-E can be configured to provide communication services to mobile and stationary devices according to instructions provided by the macro base station  4402 . In other examples of operation however, the communication nodes  4404 A-E operate merely as analog repeaters to spread the coverage of the macro base station  4402  throughout the entire range of the individual communication nodes  4404 A-E. 
     The micro base stations (depicted as communication nodes  4404 ) can differ from the macro base station in several ways. For example, the communication range of the micro base stations can be smaller than the communication range of the macro base station. Consequently, the power consumed by the micro base stations can be less than the power consumed by the macro base station. The macro base station optionally directs the micro base stations as to which mobile and/or stationary devices they are to communicate with, and which carrier frequency, spectral segment(s) and/or timeslot schedule of such spectral segment(s) are to be used by the micro base stations when communicating with certain mobile or stationary devices. In these cases, control of the micro base stations by the macro base station can be performed in a master-slave configuration or other suitable control configurations. Whether operating independently or under the control of the macro base station  4402 , the resources of the micro base stations can be simpler and less costly than the resources utilized by the macro base station  4402 . 
     Turning now to  FIG. 44B , a block diagram illustrating an example, non-limiting embodiment of the communication nodes  4404 B-E of the communication system  4400  of  FIG. 44A  is shown. In this illustration, the communication nodes  4404 B-E are placed on a utility fixture such as a light post. In other embodiments, some of the communication nodes  4404 B-E can be placed on a building or a utility post or pole that is used for distributing power and/or communication lines. The communication nodes  4404 B-E in these illustrations can be configured to communicate with each other over the interface  4410 , which in this illustration is shown as a wireless interface. The communication nodes  4404 B-E can also be configured to communicate with mobile or stationary devices  4406 A-C over a wireless interface  4411  that conforms to one or more communication protocols (e.g., fourth generation (4G) wireless signals such as LTE signals or other 4G signals, fifth generation (5G) wireless signals, WiMAX, 802.11 signals, ultra-wideband signals, etc.). The communication nodes  4404  can be configured to exchange signals over the interface  4410  at an operating frequency that is may be higher (e.g., 28 GHz, 38 GHz, 60 GHz, 80 GHz or higher) than the operating frequency used for communicating with the mobile or stationary devices (e.g., 1.9 GHz) over interface  4411 . The high carrier frequency and a wider bandwidth can be used for communicating between the communication nodes  4404  enabling the communication nodes  4404  to provide communication services to multiple mobile or stationary devices via one or more differing frequency bands, (e.g. a 900 MHz band, 1.9 GHz band, a 2.4 GHz band, and/or a 5.8 GHz band, etc.) and/or one or more differing protocols. In other embodiments, particularly where the interface  4410  is implemented via a guided wave communications system on a wire, a wideband spectrum in a lower frequency range (e.g. in the range of 2-6 GHz, 4-10 GHz, etc.) can be employed. 
     Turning now to  FIG. 44C , a block diagram illustrating an example, non-limiting embodiment of downlink and uplink communication techniques for enabling a base station to communicate with the communication nodes  4404  of  FIG. 44A  is shown. In the illustrations of  FIG. 44C , downlink signals (i.e., signals directed from the macro base station  4402  to the communication nodes  4404 ) can be spectrally divided into control channels  4422 , downlink spectral segments  4426  each including modulated signals which can be frequency converted to their original/native frequency band (e.g., cellular band, or other native frequency band) for enabling the communication nodes  4404  to communicate with one or more mobile or stationary devices  4426 , and pilot signals  4424  which can be supplied with some or all of the spectral segments  4426  for mitigating distortion created between the communication nodes  4424 . The pilot signals  4424  can be processed by tethered or wireless transceivers of downstream communication nodes  4404  to remove distortion from a receive signal (e.g., phase distortion). Each downlink spectral segment  4426  can be allotted a bandwidth  4425  sufficiently wide (e.g., 50 MHz) to include a corresponding pilot signal  4424  and one or more downlink modulated signals located in frequency channels (or frequency slots) in the spectral segment  4426 . The modulated signals can represent cellular channels, WLAN channels or other modulated communication signals (e.g., 10-20 MHz), which can be used by the communication nodes  4404  for communicating with one or more mobile or stationary devices  4406 . 
     Uplink modulated signals generated by mobile or stationary communication devices in their native/original frequency bands (e.g., cellular band, or other native frequency band) can be frequency converted and thereby located in frequency channels (or frequency slots) in the uplink spectral segment  4430 . The uplink modulated signals can represent cellular channels, WLAN channels or other modulated communication signals. Each uplink spectral segment  4430  can be allotted a similar or same bandwidth  4425  to include a pilot signal  4428  which can be provided with some or each spectral segment  4430  to enable upstream communication nodes  4404  and/or the macro base station  4402  to remove distortion (e.g., phase error). 
     In the embodiment shown, the downlink and uplink spectral segments  4426  and  4430  each comprise a plurality of frequency channels (or frequency slots), which can be occupied with modulated signals that have been frequency converted from any number of native/original frequency bands (e.g. a 900 MHz band, 1.9 GHz band, a 2.4 GHz band, and/or a 5.8 GHz band, etc.). The modulated signals can be up-converted to adjacent frequency channels in downlink and uplink spectral segments  4426  and  4430 . In this fashion, while some adjacent frequency channels in a downlink spectral segment  4426  can include modulated signals originally in a same native/original frequency band, other adjacent frequency channels in the downlink spectral segment  4426  can also include modulated signals originally in different native/original frequency bands, but frequency converted to be located in adjacent frequency channels of the downlink spectral segment  4426 . For example, a first modulated signal in a 1.9 GHz band and a second modulated signal in the same frequency band (i.e., 1.9 GHz) can be frequency converted and thereby positioned in adjacent frequency channels of a downlink spectral segment  4426 . In another illustration, a first modulated signal in a 1.9 GHz band and a second communication signal in a different frequency band (i.e., 2.4 GHz) can be frequency converted and thereby positioned in adjacent frequency channels of a downlink spectral segment  4426 . Accordingly, frequency channels of a downlink spectral segment  4426  can be occupied with any combination of modulated signals of the same or differing signaling protocols and of a same or differing native/original frequency bands. 
     Similarly, while some adjacent frequency channels in an uplink spectral segment  4430  can include modulated signals originally in a same frequency band, adjacent frequency channels in the uplink spectral segment  4430  can also include modulated signals originally in different native/original frequency bands, but frequency converted to be located in adjacent frequency channels of an uplink segment  4430 . For example, a first communication signal in a 2.4 GHz band and a second communication signal in the same frequency band (i.e., 2.4 GHz) can be frequency converted and thereby positioned in adjacent frequency channels of an uplink spectral segment  4430 . In another illustration, a first communication signal in a 1.9 GHz band and a second communication signal in a different frequency band (i.e., 2.4 GHz) can be frequency converted and thereby positioned in adjacent frequency channels of the uplink spectral segment  4426 . Accordingly, frequency channels of an uplink spectral segment  4430  can be occupied with any combination of modulated signals of a same or differing signaling protocols and of a same or differing native/original frequency bands. It should be noted that a downlink spectral segment  4426  and an uplink spectral segment  4430  can themselves be adjacent to one another and separated by only a guard band or otherwise separated by a larger frequency spacing, depending on the spectral allocation in place. 
     Turning now to  FIG. 44D , a graphical diagram  4460  illustrating an example, non-limiting embodiment of a frequency spectrum is shown. In particular, a spectrum  4462  is shown for a distributed antenna system that conveys modulated signals occupying frequency channels of uplink or downlink spectral segments after they have been converted in frequency (e.g. via up-conversion or down-conversion) from one or more original/native spectral segments into the spectrum  4462 . 
     As previously discussed two or more different communication protocols can be employed to communicate upstream and downstream data. When two or more differing protocols are employed, a first subset of the downlink frequency channels of a downlink spectral segment  4426  can be occupied by frequency converted modulated signals in accordance with a first standard protocol and a second subset of the downlink frequency channels of the same or a different downlink spectral segment  4430  can be occupied by frequency converted modulated signals in accordance with a second standard protocol that differs from the first standard protocol. Likewise a first subset of the uplink frequency channels of an uplink spectral segment  4430  can be received by the system for demodulation in accordance with the first standard protocol and a second subset of the uplink frequency channels of the same or a different uplink spectral segment  4430  can be received in accordance with a second standard protocol for demodulation in accordance with the second standard protocol that differs from the first standard protocol. 
     In the example shown, the downstream channel band  4444  includes a first plurality of downstream spectral segments represented by separate spectral shapes of a first type representing the use of a first communication protocol. The downstream channel band  4444 ′ includes a second plurality of downstream spectral segments represented by separate spectral shapes of a second type representing the use of a second communication protocol. Likewise the upstream channel band  4446  includes a first plurality of upstream spectral segments represented by separate spectral shapes of the first type representing the use of the first communication protocol. The upstream channel band  4446 ′ includes a second plurality of upstream spectral segments represented by separate spectral shapes of the second type representing the use of the second communication protocol. These separate spectral shapes are meant to be placeholders for the frequency allocation of each individual spectral segment along with associated reference signals, control channels and/or clock signals. While the individual channel bandwidth is shown as being roughly the same for channels of the first and second type, it should be noted that upstream and downstream channel bands  4444 ,  4444 ′,  4446  and  4446 ′ may be of differing bandwidths. Additionally, the spectral segments in these channel bands of the first and second type may be of differing bandwidths, depending on available spectrum and/or the communication standards employed. 
     Turning now to  FIG. 44E , a graphical diagram  4470  illustrating an example, non-limiting embodiment of a frequency spectrum is shown. In particular a portion of the spectrum  4462  of  FIG. 44D  is shown for a distributed antenna system that conveys modulated signals in the form of channel signals that have been converted in frequency (e.g. via up-conversion or down-conversion) from one or more original/native spectral segments. 
     The portion  4472  includes a portion of a downlink or uplink spectral segment  4426  and  4430  that is represented by a spectral shape and that represents a portion of the bandwidth set aside for a control channel, reference signal, and/or clock signal. The spectral shape  4474 , for example, represents a control channel that is separate from reference signal  4479  and a clock signal  4478 . It should be noted that the clock signal  4478  is shown with a spectral shape representing a sinusoidal signal that may require conditioning into the form of a more traditional clock signal. In other embodiments however, a traditional clock signal could be sent as a modulated carrier wave such by modulating the reference signal  4479  via amplitude modulation or other modulation technique that preserves the phase of the carrier for use as a phase reference. In other embodiments, the clock signal could be transmitted by modulating another carrier wave or as another signal. Further, it is noted that both the clock signal  4478  and the reference signal  4479  are shown as being outside the frequency band of the control channel  4474 . 
     In another example, the portion  4475  includes a portion of a downlink or uplink spectral segment  4426  and  4430  that is represented by a portion of a spectral shape that represents a portion of the bandwidth set aside for a control channel, reference signal, and/or clock signal. The spectral shape  4476  represents a control channel having instructions that include digital data that modulates the reference signal, via amplitude modulation, amplitude shift keying or other modulation technique that preserves the phase of the carrier for use as a phase reference. The clock signal  4478  is shown as being outside the frequency band of the spectral shape  4476 . The reference signal, being modulated by the control channel instructions, is in effect a subcarrier of the control channel and is in-band to the control channel. Again, the clock signal  4478  is shown with a spectral shape representing a sinusoidal signal, in other embodiments however, a traditional clock signal could be sent as a modulated carrier wave or other signal. In this case, the instructions of the control channel can be used to modulate the clock signal  4478  instead of the reference signal. 
     Consider the following example, where the control channel  4476  is carried via modulation of a reference signal in the form of a continuous wave (CW) from which the phase distortion in the receiver is corrected during frequency conversion of the downlink or uplink spectral segment  4426  and  4430  back to its original/native spectral segment. The control channel  4476  can be modulated with a robust modulation such as pulse amplitude modulation, binary phase shift keying, amplitude shift keying or other modulation scheme to carry instructions between network elements of the distributed antenna system such as network operations, administration and management traffic and other control data. In various embodiments, the control data can include without limitation:
         Status information that indicates online status, offline status, and network performance parameters of each network element.   Network device information such as module names and addresses, hardware and software versions, device capabilities, etc.   Spectral information such as frequency conversion factors, channel spacing, guard bands, uplink/downlink allocations, uplink and downlink channel selections, etc.   Environmental measurements such as weather conditions, image data, power outage information, line of sight blockages, etc.       

     In a further example, the control channel data can be sent via ultra-wideband (UWB) signaling. The control channel data can be transmitted by generating radio energy at specific time intervals and occupying a larger bandwidth, via pulse-position or time modulation, by encoding the polarity or amplitude of the UWB pulses and/or by using orthogonal pulses. In particular, UWB pulses can be sent sporadically at relatively low pulse rates to support time or position modulation, but can also be sent at rates up to the inverse of the UWB pulse bandwidth. In this fashion, the control channel can be spread over an UWB spectrum with relatively low power, and without interfering with CW transmissions of the reference signal and/or clock signal that may occupy in-band portions of the UWB spectrum of the control channel. 
     In one or more embodiments, communication device  4510  can include an antenna array  4515  for transmitting wireless signals. In one or more embodiments, the antenna array  4515  can perform beam steering. For example, the antenna array  4515  can utilize a first subset of antennas of the antenna array to transmit first wireless signals  4525  directed (as shown by reference number  4527 ) via beam steering towards the communication device  4550 . A second subset of antennas of the antenna array  4515  can transmit second wireless signals  4530  directed (as shown by reference number  4532 ) via the beam steering towards a transmission medium  4575  (e.g., a power line connected between the utility poles  4520 ,  4560 ). In one or more embodiments, the aforementioned beams can be simultaneously created by the same set of antennas in arrays  4510  and  4550 . In one or more embodiments, the beam steering can enable the antenna array to communicate with more than one wireless receiver with or without directing wireless signals to a transmission medium. In one or more embodiments, the beam steering can enable the antenna array to direct the wireless signals to more than one transmission medium with or without communicating with a wireless receiver. 
     The first and second wireless signals  4525 ,  4530  can be associated with communication signals that are to be transmitted over the network. For instance, the first and second wireless signals  4525 ,  4530  can be the same signals. In another example, the first wireless signals  4525  can represent a first subset of the communication signals, while the second wireless signals  4530  represent a second subset of the communication signals. In one embodiment, the first and second wireless signals  4525 ,  4530  can be different and can be based on interleaving of a group of communication signals, such as video packets, and so forth. The communication signals can be various types of signals including information associated with subscriber services, network control, testing, and so forth. 
     In one or more embodiments, the second wireless signals  4530  induce electromagnetic waves  4540 . For example, the electromagnetic waves  4540  are induced at a physical interface of the transmission medium  4575  and propagate (as shown by reference number  4542 ) without requiring an electrical return path. The electromagnetic waves  4540  are guided by the transmission medium  4575  towards the communication device  4550 , which is positioned in proximity to the transmission medium. The electromagnetic waves  4575  can be representative of the second wireless signals  4530  which are associated with the communication signals. 
     In one or more embodiments, the communication device  4550  can include a receiver that is configured to receive the electromagnetic waves  4540  that are propagating along the transmission medium  4575 . Various types of receivers can be used for receiving the electromagnetic waves  4540 , such as devices shown in  FIGS. 7, 8 and 9A . System  4500  enables the communication device  4510  to transmit information which is received by the communication device  4550  (e.g., another antenna array  4555 ) via the wireless communication path  4527  and via being guided by the transmission medium  4575 . 
     In one or more embodiments, the antenna arrays  4515 ,  4555  can include polyrod antennas. For example, each of the polyrod antennas can include a core that is connected with a waveguide that is configured to confine an electromagnetic wave at least in part within the core in a particular region of the core. In one embodiment, each of the polyrod antennas can include a core having a first region, a second region, a third region, and a fourth region, where the core comprises an interface in the first region. One of the plurality of transmitters can generate a first electromagnetic wave that induces a second electromagnetic wave at the interface of the first region. The core can be connected with a waveguide that is configured to confine the second electromagnetic wave at least in part within the core in the first region, where the second region of the core is configured to reduce a radiation loss of the second electromagnetic wave as the second electromagnetic wave propagates into the second region. The third region of the core can be configured to reduce a propagation loss of the second electromagnetic wave as the second electromagnetic wave propagates into the third region. The fourth region of the core can be outside of the waveguide and can be tapered to facilitate transmitting one of the first or second wireless signals based on the second electromagnetic wave. 
     In one or more embodiments, the communication device  4510  can provide a phase adjustment to the second wireless signals  4530  to accomplish beam steering towards the transmission medium  4575 .  FIG. 45  illustrates the antenna array  4555  and the receiver  4565  being co-located at communication device  4550 , however, in another embodiment the antenna array  4555  and the receiver  4565  can be separate devices that may or may not be in proximity to each other. For example, the first wireless signals  4525  can be received by the antenna array  4555  of the communication device  4550  while the electromagnetic waves  4540  can be received by a receiver of a different communication device (not shown) that is in proximity to the transmission medium  4575 . 
       FIGS. 46A, 46B, 46C, 46D, 46E, and 46F  are graphical diagrams illustrating example, non-limiting embodiments of network configurations  4600  of waveguide systems in accordance with various aspects described herein. In the illustration of  FIG. 46A , a master waveguide system  4602  is coupled to a transmission medium  4604 , which in the present illustration, represents a physical transmission medium such as a cable (e.g., a power line supported by a utility pole). The master waveguide system  4602  can be configured to use any of the embodiments of the subject disclosure singly or in any combination. The master waveguide system  4602  can be configured, for example, to transmit electromagnetic waves  4606  that propagate on a surface of the transmission medium  4604  and are directed to a recipient waveguide system  4608 . The master waveguide system  4602  can also be configured, for example, to receive the electromagnetic waves that propagate on the surface of the transmission medium  4604  that are generated by the recipient waveguide system  4608 . 
     The recipient waveguide system  4608  can also be configured to use any of the embodiments of the subject disclosure singly or in any combination for receiving and transmitting electromagnetic waves  4606 . An access point  4607  comprising, for example, an Ethernet switch can be used for distributing to communication devices in a vicinity of the access point  4607  data extracted by the recipient waveguide system  4608  from the electromagnetic waves  4606 . The data can comprise, for example, different types of communication signals including without limitation voice communication signals, video streaming signals, and/or non-real-time communication signals conveying data. 
     The master waveguide system  4602  and the recipient waveguide system  4608  can be configured to use a power supply that inductively obtains energy from the transmission medium  4604  (e.g., a medium voltage power line delivering energy between 1 kV-69 kV) to power the components of the master waveguide system  4602  and the recipient waveguide system  4608 . The master waveguide system  4602  and the recipient waveguide system  4608  can also be configured with a battery backup supply to mitigate the effects of a power outage. The access point  4607 , on the other hand, can be configured to couple to a low voltage line such as 220 V to power its components, and can also be configured with a battery backup supply to mitigate a power outage. 
     The master waveguide system  4602  and the recipient waveguide system  4608  can be configured to send and receive low-power ultra-wideband (UWB) electromagnetic wave pulses (e.g., UWB pulses operating at millimeter-wave frequencies at low energy such as, for example, nano-watts). In one embodiment, for example, the master waveguide system  4602  and the recipient waveguide system  4608  can be configured with a transmitter  4610  (see  FIG. 46G ) and receiver  4620  (see  FIG. 46  J) for transmitting and receiving low-power UWB electromagnetic wave pulses, respectively. In one embodiment, the transmitter  4610  and receiver  4620  can be configured to transmit and receive communication signals without demodulating or re-modulating an original modulation scheme used for generating the communication signal. For example, the transmitter  4610  and receiver  4620  can be configured to transmit and receive signals without demodulating or re-modulating an original modulation scheme. In various embodiments, the signals may be formatted as LTE signals (e.g., in accordance with orthogonal frequency-division multiple access, generally, referred to as OFDMA; or single carrier frequency-division multiple access, generally, referred to as SC-FDMA) however, signals formatted in conjunction with other communication protocols can likewise be employed. Configuring the transmitter  4610  and receiver  4620  to maintain the original modulation scheme can simplify an implementation of the transmitter  4610  and receiver  4620 , which helps reduce cost and power consumption of the master waveguide system  4602  and the recipient waveguide system  4608 . 
     For instance, in  FIG. 46G , the transmitter  4610  can be configured with an analog-to-digital converter (ADC)  4613  to sample an original signal  4612  (e.g. an LTE signal or other signal formatted in accordance with a communication protocol) at a sampling rate such as the Nyquist rate. Assuming the original signal  4612  has a 10 MHz bandwidth centered at 2 GHz, a sampling rate of at least 20 MHz can be used to produce digital word samples of the original signal (e.g., 16 bit words) every 50 ns, however in other embodiments, oversampling the RF frequency of the original signal  4612  can be employed to, for example, preserve the phase of the original signal  4612 . Each digital word sample represents a voltage value of the original signal  4612  during a specific sampling time. An ultra-wideband (UWB) pulse generator  4616  can be configured with RF circuitry (such as a mixer, amplifier, antenna) to send time domain UWB pulses, each UWB pulse representative of each bit in the digital word sample. The UWB pulse generator  4616  can be configured, for example, to use a reference signal of 60 GHz to enable the transmission of a 60 GHz pulse that corresponds in the present illustration to two cycles of a sign wave. At 60 GHz this represents a pulse width in the time domain of 33 ps. In one embodiment, the UWB pulse generator  4616  can be configured to transmit a pulse when a bit in the digital word is a “1”, and no pulse when the bit in the digital word is a “0”.  FIG. 46G  illustrates a pulse train  4618  of 8 time-domain pulses representing 8 bits in the 16 bit digital word with “1&#39;s”. Each time-domain pulse illustrated in  FIG. 46G  corresponds to a two cycle sine wave at 60 GHz (33 ps pulse). The pulse train  4618  also illustrates  8  intermingled slots of 33 ps with no energy representative of 8 bits in the 16 bit digital word with “0&#39;s”. This is, of course, an illustration and any combination of “1&#39;s” and “0&#39;s” is possible. 
     In an alternative embodiment, the UWB pulse generator  4616  can be configured to use phase modulation (e.g., binary phase-shift keying or binary PSK). In this embodiment, the UWB pulse generator  4616  would always generate 16 time-domain pulses, each having a width of 33 ps. The UWB pulses, however, may have differing phases. Other modulation techniques for transmitting and receiving UWB electromagnetic wave pulses are contemplated by the subject disclosure. 
     The pulse train  4618  shown in  FIG. 46G  occupies approximately a 0.5 ns slot (33 ps*16) as shown in  FIG. 46H . Since the ADC  4613  produces samples at a rate of one 16 bit digital word sample every 50 ns, there is a period of approximately, 45.5 ns after the pulse train  4618  where no UWB pulses are transmitted until the next 16 bit digital word sample. The 45.5 ns period can be used for time-division multiplexing (TDM) of downstream and upstream communications, thereby enabling two or more waveguide systems to perform bidirectional communications. For example, in  FIG. 46I , communication node A can be configured to transmit signals in time slot  1  (TS 1 ) and communication node B can be configured to transmit signals in time slot  2  (TS 2 ). In this configuration, communication node A and communication node B can engage in simultaneous bidirectional communications during each 50 ns sampling period. Communication nodes A and B can also be assigned to multiple time slots, respectively, to enable multiple streams of transmissions, each transmission stream associated with one of a plurality of communication signals (e.g., one of a plurality LTE signals). Communication nodes A and B can represent the master waveguide system  4602  and the recipient waveguide system  4608  of FIG. A (or other combination of waveguide systems shown in  FIGS. 46A-46F ). 
       FIG. 46J  illustrates an embodiment for a receiver  4620  that can be configured to receive the pulse train  4618  generated by the transmitter  4610  of  FIG. 46  G, and to obtain an original signal  4612  therefrom (e.g., the original signal sampled by the transmitter  4610  of  FIG. 46G ). In this embodiment, an RF detector  4622  (e.g., a crystal diode, envelope detector or other detector) can be configured to detect the pulse train  4618  of UWB pulses at a center frequency of 60 GHz and to convert the UWB pulses to baseband pulses  4624  of digital bits (i.e., “1&#39;s” and “0&#39;s”). In particular, when a pulse in the pulse train  4618  is detected by the RF detector  4622 , a digital “1” pulse is generated, while when no pulse is detected a digital “0” pulse is generated. A word converter  4626  (e.g., serial to parallel converter) can be used to generate 16 bit digital words that are supplied to a digital-to-analog converter (DAC)  4626  set to a Nyquist sampling rate equal to the sampling rate used by the ADC  4613  of the transmitter  4610  of  FIG. 46G . Upon receiving 16 bit digital words from the word converter  4626 , the DAC  4626  generates discrete analog samples  4628  of the original signal  4612 . The discrete analog samples  4628  can then be supplied to a bandpass filter (BPF)  4629  which is configured with a passband equal to the bandwidth of the original signal  4612  (e.g., 10 MHz) and centered at the carrier frequency of the original signal  4612  (e.g., 2 GHz). The filtering performed by the BPF  4629  restores the original signal  4612 . 
     Based on the illustrations of  FIGS. 46G-46J , the master waveguide system  4602  and the recipient waveguide system  4608  of  FIG. 46A  can be configured with the transmitter  4610  and the receiver  4620  described above. Accordingly, a transmitter  4610  of the master waveguide system  4602  can be configured, according to the embodiments described above, to transmit a pulse train  4618  (represented by surface wave  4606 ), which is directed to a downstream recipient waveguide system  4608 . A receiver  4620  of the recipient waveguide system  4608  can in turn be configured to extract, according to the embodiments described above, the original signal  4612  (e.g., LTE signal or other signal) from the pulse train  4618 , and provide the original signal  4612  to the access point  4607  (via a cable or wireless interface such as infrared or other wireless technology). The access point  4607  can in turn wirelessly distribute the original signal  4612  (e.g., LTE signal or other signal) to a communication device in a vicinity of the access point  4607 . 
     Alternatively, the recipient waveguide system  4608  can be configured to retransmit the pulse train  4618  with the assistance of another waveguide system  4608 ′ managing another span of the transmission medium (e.g., power line). To accomplish this, the recipient waveguide system  4608  can provide the pulse train  4618  (wirelessly or via a cable) to the other waveguide system  4608 ′ managing the other span. The other waveguide system  4608 ′ can be configured to perform signal conditioning (e.g., amplifying, filtering) of the pulse train  4618 . Once reconditioned, the other waveguide system  4608 ′ can retransmit the reconditioned pulse train  4618  (represented by surface wave  4606 ) to another downstream recipient waveguide system  4608 , which can be configured to either retransmit the pulse train  4618  using another waveguide system  4608 ′ as described above, or provide an extracted original signal  4612  to the access point  4607  for wireless distribution to a local communication device. 
     It will be appreciated that the transmitter  4610  of  FIG. 46G  and the receiver  4620  of  FIG. 46J  can be adapted according to other embodiments. For example, if phase modulation is used (e.g., binary-PSK), the UWB pulse generator  4616  can also be configured to send a reference signal to a receiver  4620  for purposes of synchronization and phase distortion mitigation. The reference signal can be a preamble of alternating “1&#39;s” and “0&#39;s”. The preamble can be sent as a separate reference signal positioned somewhere in one of the time slots shown in  FIG. 46I . The reference signal can also be combined with control information that can be used to assign time slots between pairing waveguide systems for downstream and upstream communications. Alternatively, a reference signal such as a preamble can be transmitted by robbing the least significant bit of one or more 16 bit digital word samples generated by the transmitter  4610 . The preamble in turn can be decoded at the receiver  4620  to obtain synchronization information and thereby mitigate distortion (such as phase distortion) experienced by the pulse train  4618 . 
     In yet other embodiments, the transmitter  4610  of  FIG. 46G  can be configured to use an analog sampler in place of the DAC  4613  (i.e., equivalent to removing the digital conversion circuitry of the DAC). The analog sampler can in turn generate discrete analog samples, each analog sample representing a voltage of the original signal  4612 , and each analog sample being generated at a sampling cycle of 50 ns. The UWB pulse generator  4616  can in turn generate time domain UWB pulses (of two 60 GHz sine wave cycles) having an amplitude approximately equal to the voltage of each discrete analog sample. Hence, the UWB pulses no longer represent digital bits, but rather voltage samples of the original signal  4612 . The receiver  4620  can in turn be configured to use an RF detector  4622  that regenerates the discrete analog samples at baseband. The word converter  4626  and the DAC  4626  would no longer be necessary. Instead the discrete analog samples generated by the RF detector  4622  can be supplied to the BPF  4629  which reconstructs the original signal  4612 . 
     It will be appreciated that the transmitter  4610  and receiver  4620  of  FIGS. 46G and 46J  can be configured with an antenna, one or more amplifiers, one or more filters, and other circuitry to transmit and receive wireless UWB electromagnetic wave pulses that propagate between communication nodes in a wireless transmission medium (e.g., air). It will be further appreciated that other UWB pulse modulation techniques for transmitting and receiving UWB pulses (wireless or surface waves) is contemplated by the subject disclosure. 
     Referring back to  FIG. 46G , it will also be appreciated that the surface waves  4606  can be accompanied with a control channel that can be used to instruct the waveguide systems  4608  to retransmit or extract original signals  4612  for subsequent distribution by a corresponding access point  4607  to a local communication device. The control channel can be transmitted in a separate time slot (shown in  FIG. 46I ) as a pulse train  4618  of UWB electromagnetic wave pulses. In other embodiments, the control channel can be intermixed with the preamble of UWB pulses described earlier, which itself can occupy its own time slot. Alternatively, a control channel can be transmitted without intermixing it with the preamble, but instead by robbing one or more least significant bits from one or more time slots used for data communications between waveguide systems  4608 . Other embodiments for transmitting preambles and one or more control channels are contemplated by the subject disclosure. 
     Referring back to  FIG. 46A , a waveguide system  4608 ′ is shown transmitting a pulse train  4618  represented by surface wave  4606  over two spans without a waveguide repeater (e.g., a waveguide system  4608  paired with another waveguide system  4608 ′) at the third utility pole  4605 . If, however, a distance of two or more spans results in significant propagation losses in the pulse train  4618 , which prevents the pulse train  4618  from successfully reaching the next waveguide system  4608 , then a waveguide repeater can be placed at the third utility pole  4605  to enable retransmissions to the next span as shown in  FIG. 46B . 
     Turning now to  FIGS. 46C-46F , the network configurations  4600  of the waveguide systems of  FIG. 46A  can be adapted with waveguide system  4609  paired with waveguide system  4609 ′ on a parallel span as shown in  FIG. 46C . Utilizing the additional span for exchanging surface waves  4606 ′ can provide additional transmission bandwidth. An additional span can also provide backup spans if one or more waveguide systems fail, and/or a fault (e.g., an obstruction) is detected on a particular span that prevents the exchange of surface waves  4606  or  4606 ′. Traffic from one span can be redirected to a parallel span by configuring a waveguide system  4608  to transmit (wirelessly or over a cable) the pulse train  4618  to a neighboring waveguide system  4609 , and vice-versa. If propagation losses are two high for propagating surface waves  4606  or  4606 ′ over two spans, repeaters can be added to the third utility pose  4605  as shown in  FIG. 46D .  FIG. 46E  illustrates a situation where no faults are detected on either of the parallel spans enabling surface waves  4606  and  4606 ′ to propagate along the parallel spans. When a fault is detected, such as shown in  FIG. 46F  illustrated as a “Broken Surface-Wave”, the waveguide system  4608  of the broken span can be configured to redirect traffic to a neighboring waveguide system  4609  on the alternate span. 
       FIG. 46K  illustrates a flow diagram of an example, non-limiting embodiment of a method  4630  for transmitting ultra-wideband (UWB) electromagnetic pulses based on a communication signal in accordance with various aspects described herein. Method  4630  can begin with step  4632  in which a system can be configured to receive a communication signal. The system can be a waveguide system or a coupling device that can receive and process the communication signal to generate at step  4634  UWB pulses according to the communication signal. The communication signal can be baseband signals that convey data such as voice, video streams, or non-real data exchanges. The communication signal can also represent modulated signals (e.g., cellular LTE, 5G signals or other signals) in a corresponding frequency band. As noted in the descriptions of  FIGS. 46G-46J  such communication signals can be converted by a transmitter  4610  to pulse trains  4618  of UWB pulses without modifying the modulation scheme of the communication signals. The transmitter  4610  can in turn transmit the pulse train  4618  at step  4636  as UWB pulses represented by a surface wave  4606  or  4606 ′ that propagates on a physical transmission medium (e.g., reference  4604 ), or wireless UWB pulses that propagate in a wireless transmission medium such as air. 
       FIG. 46L  illustrates a flow diagram of an example, non-limiting embodiment of a method  4640  for receiving UWB electromagnetic pulses and generating therefrom a communication signal in accordance with various aspects described herein. Method  4640  can begin with step  4642  where a receiver  4620  such as shown in  FIG. 46J  is configured to receive a pulse train  4618  of UWB pulses represented by surface wave  4606  or  4606 ′. In one embodiment, the receiver  4620  can be configured to obtain at step  4644  one or more communication signals from the pulse train  4618 , and provide at step  4646  the one or more communication signals to one or more corresponding communication devices wirelessly via an access point  4607 , as previously described. Alternatively, the receiver  4620  can be configured to retransmit at step  4648  the pulse train  4618  of UWB pulses to a downstream receiver. The receiver  4620  can retransmit the pulse train  4618  by providing it to a repeater that reconditions the UWB pulse before retransmission. 
     It will be appreciated that the master waveguide system  4602  and the recipient waveguide systems  4608  can be adapted to transmit and/or receive UWB electromagnetic waves that propagate on a surface of a transmission medium (e.g.,  4604  and  4604 ′) in place of UWB pulses transmitted or received via a surface of a transmission medium. It will be further appreciated that the master waveguide system  4602  and the recipient waveguide systems  4608  can also be configured to transmit or receive UWB electromagnetic waves (or UWB pulses) that satisfy a Part 15 rule for radio frequency devices promulgated by the Federal Communications Commission (FCC). For example, the master waveguide system  4602  and the recipient waveguide systems  4608  can be adapted to transmit or receive UWB electromagnetic waves (or UWB pulses) having a bandwidth that is one-fifth of a center frequency of the surface wave or 200 MHz or greater to satisfy the FCC&#39;s Part 15 rule. Additionally, the master waveguide system  4602  and the recipient waveguide systems  4608  can be configured to transmit such UWB electromagnetic waves (or UWB pulses) at low power (e.g., less than 1 micro-watt). Accordingly, a waveguide system that transmits or receives UWB electromagnetic waves (or UWB pulses) conforming to the FCC&#39;s Part 15 rule can operate without a license from the FCC. 
     Obstructions along a span  4604  of a transmission medium can cause propagation losses of UWB electromagnetic waves (or UWB pulses). For example, UWB electromagnetic waves (or UWB pulses) can experience propagation losses when they traverse a supporting device or supporting structure such as an electrical insulator (e.g., ceramic insulator)  4611  located at each end of a utility pole  4605  used to support both ends of a span  4604  (see  FIGS. 46A-46F ). To avoid such obstructions, the master waveguide system  4602  can be positioned after an electrical insulator  4611  holding a first end of the span  4604  at a first utility pole  4605 , while the recipient waveguide system  4608  can be positioned before the electrical insulator  4611  holding a second end of the span  4604  at a second utility pole  4605 . By placing a master waveguide system  4602  and a corresponding recipient waveguide system  4608  in these positions, the UWB electromagnetic waves (or UWB pulses) exchanged between the master waveguide system  4602  and the recipient waveguide system  4608  can avoid traversing the electrical insulators  4611  and thereby circumvent the propagation losses that the UWB electromagnetic waves (or UWB pulses) would have otherwise experienced. The foregoing technique can be used with two recipient waveguide systems  4608  located at both ends of a span  4604 ; that is, after and before their respective electrical insulators  4611 . 
     Two recipient waveguide systems  4608  positioned close to each other (e.g., 4-6 feet from each other) on both sides of an electrical insulator  4611  of a single utility pole  4605  can be configured to communicate with each other via a cable or wirelessly to avoid exchanging surface wave signals that traverse the electrical insulator  4611  located between the two recipient waveguide systems  4608 . The two recipient waveguide systems  4608  positioned between the electrical insulator  4611  of the single utility pole  4605  can also be configured to exchange signals over a cable or wirelessly at unlicensed frequencies (e.g., in a range of 57 GHz-64 GHz). 
     It will be further appreciated that the access points  4607  shown in  FIGS. 46A-46F  can be configured to perform downlink drops, uplink reception, and transfer of communication signals from one frequency channel to another frequency channel. During downlink drops, a waveguide system can provide an access point  4607  one or more communication signals conveyed by UWB electromagnetic waves (or UWB pulses) it has received. The access point  4607  in turn can transmit such signals wirelessly to communication devices. Alternatively, a waveguide system can provide an access point  4607  the UWB electromagnetic waves (or UWB pulses). In this embodiment, the access point  4607  can obtain the one or more communication signals conveyed in the UWB electromagnetic waves (or UWB pulses) and wirelessly transmit them to communication devices. In either embodiment, the waveguide system and/or the access point can perform frequency shifting of the communication signals to their native frequency bands (e.g., cellular bands) before delivering such signals wirelessly to communication devices. 
     During uplink reception, an access point  4607  can be configured to receive wireless signals from communication devices (e.g., LTE, 5G signals or otherwise) and provide electrical signals derived therefrom to a waveguide system for transport in the UWB electromagnetic waves (or UWB pulses) transmitted by the waveguide system. Prior to transmission of the UWB electromagnetic waves (or UWB pulses), the access point  4607  and/or the waveguide system can be configured to frequency shift the electrical signals for placement in frequency channels of the UWB electromagnetic waves (or UWB pulses). 
     To reduce cost and power consumption, the recipient waveguide systems  4608  can be configured to use the access point  4607  to transfer signals supplied by the recipient waveguide system  4608  from one frequency channel to another frequency channel. For example, a first recipient waveguide system  4608  that receives UWB electromagnetic waves (or UWB pulses) from a first span can provide the UWB electromagnetic waves (or UWB pulses) or electrical signals derived therefrom to the access point  4607 . The UWB electromagnetic waves (or UWB pulses) can include a plurality of frequency channels, each frequency channel conveying a communication signal. The access point  4607  can be configured to transfer a communication signal in one frequency channel to another available frequency channel. Once the transfer is completed, the access point  4607  can provide updated UWB electromagnetic waves (or UWB pulses) or electrical signals to a second recipient waveguide system  4608  that can be configured to transmit the updated UWB electromagnetic waves (or UWB pulses) on a second span  4604 . 
     The transfer of signals between frequency channels can be performed by the access point  4607  with switching technology (e.g., an Ethernet switch). To support the power necessary to operate switching technology, the access point  4607  can be configured to obtain power from a low voltage line located on the utility pole (e.g., 220 V). The recipient waveguide system  4607 , on the other hand, can be coupled to a medium voltage power line (e.g., 1000 Volts or higher). The recipient waveguide system  4608  can be designed to consume low power (e.g., 1-2 Watts) by, for example, configuring the recipient waveguide system  4607  to rely on the switching technology of the access point  4607  to transfer signals between channels of a high frequency UWB signal. Accordingly, the recipient waveguide system  4608  can be configured to use a structurally small inductive power supply that can obtain power (e.g., 1-2 Watts) from a medium voltage power line. 
     It will be appreciated that the foregoing embodiments are applicable to the master waveguide system  4602 ′, recipient waveguide systems  4609  and  4609 ′ respectively, and the transmission medium  4604 ′ shown in  FIGS. 46C-46F . 
       FIG. 46M  illustrates a flow diagram of an example, non-limiting embodiment of a method  4650  for transmitting ultra-wideband (UWB) electromagnetic waves based on a communication signal in accordance with various aspects described herein. Method  4650  can begin with step  4652  in which a system can be configured to receive a communication signal. The system can be a waveguide system or a coupling device that can receive and process the communication signal to generate at step  4654  UWB electromagnetic waves according to the communication signal. The communication signal can be baseband signals that convey data such as voice, video streams, or non-real data exchanges. The communication signal can also represent modulated signals (e.g., cellular LTE, 5G signals or other signals) in a corresponding frequency band. The communication signals can be converted (e.g., frequency-shifted) by a transmitter described in the subject disclosure to UWB electromagnetic waves without modifying the modulation scheme of the communication signals. The transmitter  4610  can in turn transmit the UWB electromagnetic waves at step  4656  as a surface wave  4606  or  4606 ′ that propagates on a physical transmission medium (e.g., reference  4604  or  4604 ′). 
       FIG. 46N  illustrates a flow diagram of an example, non-limiting embodiment of a method  4660  for receiving UWB electromagnetic waves and generating therefrom one or more communication signals in accordance with various aspects described herein. Method  4660  can begin with step  4662  where a receiver such as described in the subject disclosure is configured to receive UWB electromagnetic waves that propagate as surface waves  4606  or  4606 ′. In one embodiment, the receiver can be configured to obtain at step  4664  one or more communication signals from the UWB electromagnetic waves, and provide at step  4666  the one or more communication signals to one or more corresponding communication devices wirelessly via an access point  4607 , as previously described. Alternatively, the receiver can be configured to retransmit at step  4668  at a portion of the UWB electromagnetic waves to a downstream receiver. The receiver  4620  can retransmit the portion of the UWB electromagnetic waves by providing it to a repeater that reconditions the UWB electromagnetic waves before retransmission. 
     While for purposes of simplicity of explanation, the respective processes are shown and described as a series of blocks in  FIGS. 46K through 46N , respectively, it is to be understood and appreciated that the claimed subject matter is not limited by the order of the blocks, as some blocks may occur in different orders and/or concurrently with other blocks from what is depicted and described herein. Moreover, not all illustrated blocks may be required to implement the methods described herein. 
     It will be appreciated that the transmitter  4610  and receiver  4610  can be collocated on the same device. It will be further appreciated that the network configurations  4600  of the waveguide systems shown in  FIGS. 46A, 46B, 46C, 46D, 46E , and  46 F can be represented by couplers/launchers (as described in the subject disclosure) that can be adapted to transmit and/or receive surface waves and/or wireless signals. The couplers/launchers can be configured, for example, to transmit and/or receive UWB electromagnetic wave pulses that propagate on a surface of a physical transmission medium such as the cable described in the subject disclosure, and/or can be configured to transmit and/or receive wireless UWB electromagnetic wave pulses that propagate over a wireless transmission medium such as air. Accordingly, any of the couplers/launchers, transmitters, receivers, antennas or other devices described in the subject disclosure which can be configured to transmit and/or receive ultra-wideband electromagnetic wave pulses that propagate on a surface of a physical transmission medium or that propagate as wireless ultra-wideband electromagnetic wave pulses over a wireless transmission medium such as air can be used to perform the embodiments of  FIGS. 46A-46L  described earlier. It will be further appreciated that any of the embodiments of the subject disclosure can be adapted or modified in whole or in part to use the embodiment described in  FIGS. 46A-46L . 
     Referring now to  FIG. 47 , there is illustrated a block diagram of a computing environment in accordance with various aspects described herein. In order to provide additional context for various embodiments of the embodiments described herein,  FIG. 47  and the following discussion are intended to provide a brief, general description of a suitable computing environment  4700  in which the various embodiments of the subject disclosure can be implemented. While the embodiments have been described above in the general context of computer-executable instructions that can run on one or more computers, those skilled in the art will recognize that the embodiments can be also implemented in combination with other program modules and/or as a combination of hardware and software. 
     Generally, program modules comprise routines, programs, components, data structures, etc., that perform particular tasks or implement particular abstract data types. Moreover, those skilled in the art will appreciate that the inventive methods can be practiced with other computer system configurations, comprising single-processor or multiprocessor computer systems, minicomputers, mainframe computers, as well as personal computers, hand-held computing devices, microprocessor-based or programmable consumer electronics, and the like, each of which can be operatively coupled to one or more associated devices. 
     As used herein, a processing circuit includes processor as well as other application specific circuits such as an application specific integrated circuit, digital logic circuit, state machine, programmable gate array or other circuit that processes input signals or data and that produces output signals or data in response thereto. It should be noted that while any functions and features described herein in association with the operation of a processor could likewise be performed by a processing circuit. 
     The terms “first,” “second,” “third,” and so forth, as used in the claims, unless otherwise clear by context, is for clarity only and doesn&#39;t otherwise indicate or imply any order in time. For instance, “a first determination,” “a second determination,” and “a third determination,” does not indicate or imply that the first determination is to be made before the second determination, or vice versa, etc. 
     The illustrated embodiments of the embodiments herein can be also practiced in distributed computing environments where certain tasks are performed by remote processing devices that are linked through a communications network. In a distributed computing environment, program modules can be located in both local and remote memory storage devices. 
     Computing devices typically comprise a variety of media, which can comprise computer-readable storage media and/or communications media, which two terms are used herein differently from one another as follows. Computer-readable storage media can be any available storage media that can be accessed by the computer and comprises both volatile and nonvolatile media, removable and non-removable media. By way of example, and not limitation, computer-readable storage media can be implemented in connection with any method or technology for storage of information such as computer-readable instructions, program modules, structured data or unstructured data. 
     Computer-readable storage media can comprise, but are not limited to, random access memory (RAM), read only memory (ROM), electrically erasable programmable read only memory (EEPROM), flash memory or other memory technology, compact disk read only memory (CD-ROM), digital versatile disk (DVD) or other optical disk storage, magnetic cassettes, magnetic tape, magnetic disk storage or other magnetic storage devices or other tangible and/or non-transitory media which can be used to store desired information. In this regard, the terms “tangible” or “non-transitory” herein as applied to storage, memory or computer-readable media, are to be understood to exclude only propagating transitory signals per se as modifiers and do not relinquish rights to all standard storage, memory or computer-readable media that are not only propagating transitory signals per se. 
     Computer-readable storage media can be accessed by one or more local or remote computing devices, e.g., via access requests, queries or other data retrieval protocols, for a variety of operations with respect to the information stored by the medium. 
     Communications media typically embody computer-readable instructions, data structures, program modules or other structured or unstructured data in a data signal such as a modulated data signal, e.g., a carrier wave or other transport mechanism, and comprises any information delivery or transport media. The term “modulated data signal” or signals refers to a signal that has one or more of its characteristics set or changed in such a manner as to encode information in one or more signals. By way of example, and not limitation, communication media comprise wired media, such as a wired network or direct-wired connection, and wireless media such as acoustic, RF, infrared and other wireless media. 
     With reference again to  FIG. 47 , the example environment  4700  for transmitting and receiving signals via or forming at least part of a base station (e.g., base station devices  1504 , macrocell site  1502 , or base stations  1614 ) or central office (e.g., central office  1501  or  1611 ). At least a portion of the example environment  4700  can also be used for transmission devices  101  or  102 . The example environment can comprise a computer  4702 , the computer  4702  comprising a processing unit  4704 , a system memory  4706  and a system bus  4708 . The system bus  4708  couple&#39;s system components including, but not limited to, the system memory  4706  to the processing unit  4704 . The processing unit  4704  can be any of various commercially available processors. Dual microprocessors and other multiprocessor architectures can also be employed as the processing unit  4704 . 
     The system bus  4708  can be any of several types of bus structure that can further interconnect to a memory bus (with or without a memory controller), a peripheral bus, and a local bus using any of a variety of commercially available bus architectures. The system memory  4706  comprises ROM  4710  and RAM  4712 . A basic input/output system (BIOS) can be stored in a non-volatile memory such as ROM, erasable programmable read only memory (EPROM), EEPROM, which BIOS contains the basic routines that help to transfer information between elements within the computer  4702 , such as during startup. The RAM  4712  can also comprise a high-speed RAM such as static RAM for caching data. 
     The computer  4702  further comprises an internal hard disk drive (HDD)  4714  (e.g., EIDE, SATA), which internal hard disk drive  4714  can also be configured for external use in a suitable chassis (not shown), a magnetic floppy disk drive (FDD)  4716 , (e.g., to read from or write to a removable diskette  4718 ) and an optical disk drive  4720 , (e.g., reading a CD-ROM disk  4722  or, to read from or write to other high capacity optical media such as the DVD). The hard disk drive  4714 , magnetic disk drive  4716  and optical disk drive  4720  can be connected to the system bus  4708  by a hard disk drive interface  4724 , a magnetic disk drive interface  4726  and an optical drive interface  4728 , respectively. The interface  4724  for external drive implementations comprises at least one or both of Universal Serial Bus (USB) and Institute of Electrical and Electronics Engineers (IEEE) 1394 interface technologies. Other external drive connection technologies are within contemplation of the embodiments described herein. 
     The drives and their associated computer-readable storage media provide nonvolatile storage of data, data structures, computer-executable instructions, and so forth. For the computer  4702 , the drives and storage media accommodate the storage of any data in a suitable digital format. Although the description of computer-readable storage media above refers to a hard disk drive (HDD), a removable magnetic diskette, and a removable optical media such as a CD or DVD, it should be appreciated by those skilled in the art that other types of storage media which are readable by a computer, such as zip drives, magnetic cassettes, flash memory cards, cartridges, and the like, can also be used in the example operating environment, and further, that any such storage media can contain computer-executable instructions for performing the methods described herein. 
     A number of program modules can be stored in the drives and RAM  4712 , comprising an operating system  4730 , one or more application programs  4732 , other program modules  4734  and program data  4736 . All or portions of the operating system, applications, modules, and/or data can also be cached in the RAM  4712 . The systems and methods described herein can be implemented utilizing various commercially available operating systems or combinations of operating systems. Examples of application programs  4732  that can be implemented and otherwise executed by processing unit  4704  include the diversity selection determining performed by transmission device  101  or  102 . 
     A user can enter commands and information into the computer  4702  through one or more wired/wireless input devices, e.g., a keyboard  4738  and a pointing device, such as a mouse  4740 . Other input devices (not shown) can comprise a microphone, an infrared (IR) remote control, a joystick, a game pad, a stylus pen, touch screen or the like. These and other input devices are often connected to the processing unit  4704  through an input device interface  4742  that can be coupled to the system bus  4708 , but can be connected by other interfaces, such as a parallel port, an IEEE 1394 serial port, a game port, a universal serial bus (USB) port, an IR interface, etc. 
     A monitor  4744  or other type of display device can be also connected to the system bus  4708  via an interface, such as a video adapter  4746 . It will also be appreciated that in alternative embodiments, a monitor  4744  can also be any display device (e.g., another computer having a display, a smart phone, a tablet computer, etc.) for receiving display information associated with computer  4702  via any communication means, including via the Internet and cloud-based networks. In addition to the monitor  4744 , a computer typically comprises other peripheral output devices (not shown), such as speakers, printers, etc. 
     The computer  4702  can operate in a networked environment using logical connections via wired and/or wireless communications to one or more remote computers, such as a remote computer(s)  4748 . The remote computer(s)  4748  can be a workstation, a server computer, a router, a personal computer, portable computer, microprocessor-based entertainment appliance, a peer device or other common network node, and typically comprises many or all of the elements described relative to the computer  4702 , although, for purposes of brevity, only a memory/storage device  4750  is illustrated. The logical connections depicted comprise wired/wireless connectivity to a local area network (LAN)  4752  and/or larger networks, e.g., a wide area network (WAN)  4754 . Such LAN and WAN networking environments are commonplace in offices and companies, and facilitate enterprise-wide computer networks, such as intranets, all of which can connect to a global communications network, e.g., the Internet. 
     When used in a LAN networking environment, the computer  4702  can be connected to the local network  4752  through a wired and/or wireless communication network interface or adapter  4756 . The adapter  4756  can facilitate wired or wireless communication to the LAN  4752 , which can also comprise a wireless AP disposed thereon for communicating with the wireless adapter  4756 . 
     When used in a WAN networking environment, the computer  4702  can comprise a modem  4758  or can be connected to a communications server on the WAN  4754  or has other means for establishing communications over the WAN  4754 , such as by way of the Internet. The modem  4758 , which can be internal or external and a wired or wireless device, can be connected to the system bus  4708  via the input device interface  4742 . In a networked environment, program modules depicted relative to the computer  4702  or portions thereof, can be stored in the remote memory/storage device  4750 . It will be appreciated that the network connections shown are example and other means of establishing a communications link between the computers can be used. 
     The computer  4702  can be operable to communicate with any wireless devices or entities operatively disposed in wireless communication, e.g., a printer, scanner, desktop and/or portable computer, portable data assistant, communications satellite, any piece of equipment or location associated with a wirelessly detectable tag (e.g., a kiosk, news stand, restroom), and telephone. This can comprise Wireless Fidelity (Wi-Fi) and Bluetooth® wireless technologies. Thus, the communication can be a predefined structure as with a conventional network or simply an ad hoc communication between at least two devices. 
     Wi-Fi can allow connection to the Internet from a couch at home, a bed in a hotel room or a conference room at work, without wires. Wi-Fi is a wireless technology similar to that used in a cell phone that enables such devices, e.g., computers, to send and receive data indoors and out; anywhere within the range of a base station. Wi-Fi networks use radio technologies called IEEE 802.11 (a, b, g, n, ac, ag etc.) to provide secure, reliable, fast wireless connectivity. A Wi-Fi network can be used to connect computers to each other, to the Internet, and to wired networks (which can use IEEE 802.3 or Ethernet). Wi-Fi networks operate in the unlicensed 2.4 and 5 GHz radio bands for example or with products that contain both bands (dual band), so the networks can provide real-world performance similar to the basic 10BaseT wired Ethernet networks used in many offices. 
       FIG. 48  presents an example embodiment  4800  of a mobile network platform  4810  that can implement and exploit one or more aspects of the disclosed subject matter described herein. In one or more embodiments, the mobile network platform  4810  can generate and receive signals transmitted and received by base stations (e.g., base station devices  1504 , macrocell site  1502 , or base stations  1614 ), central office (e.g., central office  1501  or  1611 ), or transmission device  101  or  102  associated with the disclosed subject matter. Generally, wireless network platform  4810  can comprise components, e.g., nodes, gateways, interfaces, servers, or disparate platforms, that facilitate both packet-switched (PS) (e.g., internet protocol (IP), frame relay, asynchronous transfer mode (ATM)) and circuit-switched (CS) traffic (e.g., voice and data), as well as control generation for networked wireless telecommunication. As a non-limiting example, wireless network platform  4810  can be included in telecommunications carrier networks, and can be considered carrier-side components as discussed elsewhere herein. Mobile network platform  4810  comprises CS gateway node(s)  4822  which can interface CS traffic received from legacy networks like telephony network(s)  4840  (e.g., public switched telephone network (PSTN), or public land mobile network (PLMN)) or a signaling system #7 (SS7) network  4870 . Circuit switched gateway node(s)  4822  can authorize and authenticate traffic (e.g., voice) arising from such networks. Additionally, CS gateway node(s)  4822  can access mobility, or roaming, data generated through SS7 network  4870 ; for instance, mobility data stored in a visited location register (VLR), which can reside in memory  4830 . Moreover, CS gateway node(s)  4822  interfaces CS-based traffic and signaling and PS gateway node(s)  4818 . As an example, in a 3GPP UMTS network, CS gateway node(s)  4822  can be realized at least in part in gateway GPRS support node(s) (GGSN). It should be appreciated that functionality and specific operation of CS gateway node(s)  4822 , PS gateway node(s)  4818 , and serving node(s)  4816 , is provided and dictated by radio technology(ies) utilized by mobile network platform  4810  for telecommunication. 
     In addition to receiving and processing CS-switched traffic and signaling, PS gateway node(s)  4818  can authorize and authenticate PS-based data sessions with served mobile devices. Data sessions can comprise traffic, or content(s), exchanged with networks external to the wireless network platform  4810 , like wide area network(s) (WANs)  4850 , enterprise network(s)  4870 , and service network(s)  4880 , which can be embodied in local area network(s) (LANs), can also be interfaced with mobile network platform  4810  through PS gateway node(s)  4818 . It is to be noted that WANs  4850  and enterprise network(s)  4860  can embody, at least in part, a service network(s) like IP multimedia subsystem (IMS). Based on radio technology layer(s) available in technology resource(s)  4817 , packet-switched gateway node(s)  4818  can generate packet data protocol contexts when a data session is established; other data structures that facilitate routing of packetized data also can be generated. To that end, in an aspect, PS gateway node(s)  4818  can comprise a tunnel interface (e.g., tunnel termination gateway (TTG) in 3GPP UMTS network(s) (not shown)) which can facilitate packetized communication with disparate wireless network(s), such as Wi-Fi networks. 
     In embodiment  4800 , wireless network platform  4810  also comprises serving node(s)  4816  that, based upon available radio technology layer(s) within technology resource(s)  4817 , convey the various packetized flows of data streams received through PS gateway node(s)  4818 . It is to be noted that for technology resource(s)  4817  that rely primarily on CS communication, server node(s) can deliver traffic without reliance on PS gateway node(s)  4818 ; for example, server node(s) can embody at least in part a mobile switching center. As an example, in a 3GPP UMTS network, serving node(s)  4816  can be embodied in serving GPRS support node(s) (SGSN). 
     For radio technologies that exploit packetized communication, server(s)  4814  in wireless network platform  4810  can execute numerous applications that can generate multiple disparate packetized data streams or flows, and manage (e.g., schedule, queue, format . . . ) such flows. Such application(s) can comprise add-on features to standard services (for example, provisioning, billing, customer support . . . ) provided by wireless network platform  4810 . Data streams (e.g., content(s) that are part of a voice call or data session) can be conveyed to PS gateway node(s)  4818  for authorization/authentication and initiation of a data session, and to serving node(s)  4816  for communication thereafter. In addition to application server, server(s)  4814  can comprise utility server(s), a utility server can comprise a provisioning server, an operations and maintenance server, a security server that can implement at least in part a certificate authority and firewalls as well as other security mechanisms, and the like. In an aspect, security server(s) secure communication served through wireless network platform  4810  to ensure network&#39;s operation and data integrity in addition to authorization and authentication procedures that CS gateway node(s)  4822  and PS gateway node(s)  4818  can enact. Moreover, provisioning server(s) can provision services from external network(s) like networks operated by a disparate service provider; for instance, WAN  4850  or Global Positioning System (GPS) network(s) (not shown). Provisioning server(s) can also provision coverage through networks associated to wireless network platform  4810  (e.g., deployed and operated by the same service provider), such as the distributed antennas networks shown in  FIG. 1  that enhance wireless service coverage by providing more network coverage. Repeater devices such as those shown in  FIGS. 7, 8, and 9  also improve network coverage in order to enhance subscriber service experience by way of UE  4875 . 
     It is to be noted that server(s)  4814  can comprise one or more processors configured to confer at least in part the functionality of macro network platform  4810 . To that end, the one or more processor can execute code instructions stored in memory  4830 , for example. It is should be appreciated that server(s)  4814  can comprise a content manager  4815 , which operates in substantially the same manner as described hereinbefore. 
     In example embodiment  4800 , memory  4830  can store information related to operation of wireless network platform  4810 . Other operational information can comprise provisioning information of mobile devices served through wireless platform network  4810 , subscriber databases; application intelligence, pricing schemes, e.g., promotional rates, flat-rate programs, couponing campaigns; technical specification(s) consistent with telecommunication protocols for operation of disparate radio, or wireless, technology layers; and so forth. Memory  4830  can also store information from at least one of telephony network(s)  4840 , WAN  4850 , enterprise network(s)  4870 , or SS7 network  4860 . In an aspect, memory  4830  can be, for example, accessed as part of a data store component or as a remotely connected memory store. 
     In order to provide a context for the various aspects of the disclosed subject matter,  FIG. 48 , and the following discussion, are intended to provide a brief, general description of a suitable environment in which the various aspects of the disclosed subject matter can be implemented. While the subject matter has been described above in the general context of computer-executable instructions of a computer program that runs on a computer and/or computers, those skilled in the art will recognize that the disclosed subject matter also can be implemented in combination with other program modules. Generally, program modules comprise routines, programs, components, data structures, etc. that perform particular tasks and/or implement particular abstract data types. 
       FIG. 49  depicts an illustrative embodiment of a communication device  4900 . The communication device  4900  can serve as an illustrative embodiment of devices such as mobile devices and in-building devices referred to by the subject disclosure (e.g., in  FIGS. 15, 16A and 16B ). 
     The communication device  4900  can comprise a wireline and/or wireless transceiver  4902  (herein transceiver  4902 ), a user interface (UI)  4904 , a power supply  4914 , a location receiver  4916 , a motion sensor  4918 , an orientation sensor  4920 , and a controller  4906  for managing operations thereof. The transceiver  4902  can support short-range or long-range wireless access technologies such as Bluetooth®, ZigBee®, WiFi, DECT, or cellular communication technologies, just to mention a few (Bluetooth® and ZigBee® are trademarks registered by the Bluetooth® Special Interest Group and the ZigBee® Alliance, respectively). Cellular technologies can include, for example, CDMA-1×, UMTS/HSDPA, GSM/GPRS, TDMA/EDGE, EV/DO, WiMAX, SDR, LTE, as well as other next generation wireless communication technologies as they arise. The transceiver  4902  can also be adapted to support circuit-switched wireline access technologies (such as PSTN), packet-switched wireline access technologies (such as TCP/IP, VoIP, etc.), and combinations thereof. 
     The UI  4904  can include a depressible or touch-sensitive keypad  4908  with a navigation mechanism such as a roller ball, a joystick, a mouse, or a navigation disk for manipulating operations of the communication device  4900 . The keypad  4908  can be an integral part of a housing assembly of the communication device  4900  or an independent device operably coupled thereto by a tethered wireline interface (such as a USB cable) or a wireless interface supporting for example Bluetooth®. The keypad  4908  can represent a numeric keypad commonly used by phones, and/or a QWERTY keypad with alphanumeric keys. The UI  4904  can further include a display  4910  such as monochrome or color LCD (Liquid Crystal Display), OLED (Organic Light Emitting Diode) or other suitable display technology for conveying images to an end user of the communication device  4900 . In an embodiment where the display  4910  is touch-sensitive, a portion or all of the keypad  4908  can be presented by way of the display  4910  with navigation features. 
     The display  4910  can use touch screen technology to also serve as a user interface for detecting user input. As a touch screen display, the communication device  4900  can be adapted to present a user interface having graphical user interface (GUI) elements that can be selected by a user with a touch of a finger. The touch screen display  4910  can be equipped with capacitive, resistive or other forms of sensing technology to detect how much surface area of a user&#39;s finger has been placed on a portion of the touch screen display. This sensing information can be used to control the manipulation of the GUI elements or other functions of the user interface. The display  4910  can be an integral part of the housing assembly of the communication device  4900  or an independent device communicatively coupled thereto by a tethered wireline interface (such as a cable) or a wireless interface. 
     The UI  4904  can also include an audio system  4912  that utilizes audio technology for conveying low volume audio (such as audio heard in proximity of a human ear) and high volume audio (such as speakerphone for hands free operation). The audio system  4912  can further include a microphone for receiving audible signals of an end user. The audio system  4912  can also be used for voice recognition applications. The UI  4904  can further include an image sensor  4913  such as a charged coupled device (CCD) camera for capturing still or moving images. 
     The power supply  4914  can utilize common power management technologies such as replaceable and rechargeable batteries, supply regulation technologies, and/or charging system technologies for supplying energy to the components of the communication device  4900  to facilitate long-range or short-range portable communications. Alternatively, or in combination, the charging system can utilize external power sources such as DC power supplied over a physical interface such as a USB port or other suitable tethering technologies. 
     The location receiver  4916  can utilize location technology such as a global positioning system (GPS) receiver capable of assisted GPS for identifying a location of the communication device  4900  based on signals generated by a constellation of GPS satellites, which can be used for facilitating location services such as navigation. The motion sensor  4918  can utilize motion sensing technology such as an accelerometer, a gyroscope, or other suitable motion sensing technology to detect motion of the communication device  4900  in three-dimensional space. The orientation sensor  4920  can utilize orientation sensing technology such as a magnetometer to detect the orientation of the communication device  4900  (north, south, west, and east, as well as combined orientations in degrees, minutes, or other suitable orientation metrics). 
     The communication device  4900  can use the transceiver  4902  to also determine a proximity to a cellular, WiFi, Bluetooth®, or other wireless access points by sensing techniques such as utilizing a received signal strength indicator (RSSI) and/or signal time of arrival (TOA) or time of flight (TOF) measurements. The controller  4906  can utilize computing technologies such as a microprocessor, a digital signal processor (DSP), programmable gate arrays, application specific integrated circuits, and/or a video processor with associated storage memory such as Flash, ROM, RAM, SRAM, DRAM or other storage technologies for executing computer instructions, controlling, and processing data supplied by the aforementioned components of the communication device  4900 . 
     Other components not shown in  FIG. 49  can be used in one or more embodiments of the subject disclosure. For instance, the communication device  4900  can include a slot for adding or removing an identity module such as a Subscriber Identity Module (SIM) card or Universal Integrated Circuit Card (UICC). SIM or UICC cards can be used for identifying subscriber services, executing programs, storing subscriber data, and so on. 
     In the subject specification, terms such as “store,” “storage,” “data store,” data storage,” “database,” and substantially any other information storage component relevant to operation and functionality of a component, refer to “memory components,” or entities embodied in a “memory” or components comprising the memory. It will be appreciated that the memory components described herein can be either volatile memory or nonvolatile memory, or can comprise both volatile and nonvolatile memory, by way of illustration, and not limitation, volatile memory, non-volatile memory, disk storage, and memory storage. Further, nonvolatile memory can be included in read only memory (ROM), programmable ROM (PROM), electrically programmable ROM (EPROM), electrically erasable ROM (EEPROM), or flash memory. Volatile memory can comprise random access memory (RAM), which acts as external cache memory. By way of illustration and not limitation, RAM is available in many forms such as synchronous RAM (SRAM), dynamic RAM (DRAM), synchronous DRAM (SDRAM), double data rate SDRAM (DDR SDRAM), enhanced SDRAM (ESDRAM), Synchlink DRAM (SLDRAM), and direct Rambus RAM (DRRAM). Additionally, the disclosed memory components of systems or methods herein are intended to comprise, without being limited to comprising, these and any other suitable types of memory. 
     Moreover, it will be noted that the disclosed subject matter can be practiced with other computer system configurations, comprising single-processor or multiprocessor computer systems, mini-computing devices, mainframe computers, as well as personal computers, hand-held computing devices (e.g., PDA, phone, smartphone, watch, tablet computers, netbook computers, etc.), microprocessor-based or programmable consumer or industrial electronics, and the like. The illustrated aspects can also be practiced in distributed computing environments where tasks are performed by remote processing devices that are linked through a communications network; however, some if not all aspects of the subject disclosure can be practiced on stand-alone computers. In a distributed computing environment, program modules can be located in both local and remote memory storage devices. 
     Some of the embodiments described herein can also employ artificial intelligence (AI) to facilitate automating one or more features described herein. For example, artificial intelligence can be used in optional training controller  230  evaluate and select candidate frequencies, modulation schemes, MIMO modes, and/or guided wave modes in order to maximize transfer efficiency. The embodiments (e.g., in connection with automatically identifying acquired cell sites that provide a maximum value/benefit after addition to an existing communication network) can employ various AI-based schemes for carrying out various embodiments thereof. Moreover, the classifier can be employed to determine a ranking or priority of the each cell site of the acquired network. A classifier is a function that maps an input attribute vector, x=(x1, x2, x3, x4, . . . , xn), to a confidence that the input belongs to a class, that is, f(x)=confidence (class). Such classification can employ a probabilistic and/or statistical-based analysis (e.g., factoring into the analysis utilities and costs) to prognose or infer an action that a user desires to be automatically performed. A support vector machine (SVM) is an example of a classifier that can be employed. The SVM operates by finding a hypersurface in the space of possible inputs, which the hypersurface attempts to split the triggering criteria from the non-triggering events. Intuitively, this makes the classification correct for testing data that is near, but not identical to training data. Other directed and undirected model classification approaches comprise, e.g., naïve Bayes, Bayesian networks, decision trees, neural networks, fuzzy logic models, and probabilistic classification models providing different patterns of independence can be employed. Classification as used herein also is inclusive of statistical regression that is utilized to develop models of priority. 
     As will be readily appreciated, one or more of the embodiments can employ classifiers that are explicitly trained (e.g., via a generic training data) as well as implicitly trained (e.g., via observing UE behavior, operator preferences, historical information, receiving extrinsic information). For example, SVMs can be configured via a learning or training phase within a classifier constructor and feature selection module. Thus, the classifier(s) can be used to automatically learn and perform a number of functions, including but not limited to determining according to a predetermined criteria which of the acquired cell sites will benefit a maximum number of subscribers and/or which of the acquired cell sites will add minimum value to the existing communication network coverage, etc. 
     As used in some contexts in this application, in some embodiments, the terms “component,” “system” and the like are intended to refer to, or comprise, a computer-related entity or an entity related to an operational apparatus with one or more specific functionalities, wherein the entity can be either hardware, a combination of hardware and software, software, or software in execution. As an example, a component may be, but is not limited to being, a process running on a processor, a processor, an object, an executable, a thread of execution, computer-executable instructions, a program, and/or a computer. By way of illustration and not limitation, both an application running on a server and the server can be a component. One or more components may reside within a process and/or thread of execution and a component may be localized on one computer and/or distributed between two or more computers. In addition, these components can execute from various computer readable media having various data structures stored thereon. The components may communicate via local and/or remote processes such as in accordance with a signal having one or more data packets (e.g., data from one component interacting with another component in a local system, distributed system, and/or across a network such as the Internet with other systems via the signal). As another example, a component can be an apparatus with specific functionality provided by mechanical parts operated by electric or electronic circuitry, which is operated by a software or firmware application executed by a processor, wherein the processor can be internal or external to the apparatus and executes at least a part of the software or firmware application. As yet another example, a component can be an apparatus that provides specific functionality through electronic components without mechanical parts, the electronic components can comprise a processor therein to execute software or firmware that confers at least in part the functionality of the electronic components. While various components have been illustrated as separate components, it will be appreciated that multiple components can be implemented as a single component, or a single component can be implemented as multiple components, without departing from example embodiments. 
     Further, the various embodiments can be implemented as a method, apparatus or article of manufacture using standard programming and/or engineering techniques to produce software, firmware, hardware or any combination thereof to control a computer to implement the disclosed subject matter. The term “article of manufacture” as used herein is intended to encompass a computer program accessible from any computer-readable device or computer-readable storage/communications media. For example, computer readable storage media can include, but are not limited to, magnetic storage devices (e.g., hard disk, floppy disk, magnetic strips), optical disks (e.g., compact disk (CD), digital versatile disk (DVD)), smart cards, and flash memory devices (e.g., card, stick, key drive). Of course, those skilled in the art will recognize many modifications can be made to this configuration without departing from the scope or spirit of the various embodiments. 
     In addition, the words “example” and “exemplary” are used herein to mean serving as an instance or illustration. Any embodiment or design described herein as “example” or “exemplary” is not necessarily to be construed as preferred or advantageous over other embodiments or designs. Rather, use of the word example or exemplary is intended to present concepts in a concrete fashion. As used in this application, the term “or” is intended to mean an inclusive “or” rather than an exclusive “or”. That is, unless specified otherwise or clear from context, “X employs A or B” is intended to mean any of the natural inclusive permutations. That is, if X employs A; X employs B; or X employs both A and B, then “X employs A or B” is satisfied under any of the foregoing instances. In addition, the articles “a” and “an” as used in this application and the appended claims should generally be construed to mean “one or more” unless specified otherwise or clear from context to be directed to a singular form. 
     Moreover, terms such as “user equipment,” “mobile station,” “mobile,” subscriber station,” “access terminal,” “terminal,” “handset,” “mobile device” (and/or terms representing similar terminology) can refer to a wireless device utilized by a subscriber or user of a wireless communication service to receive or convey data, control, voice, video, sound, gaming or substantially any data-stream or signaling-stream. The foregoing terms are utilized interchangeably herein and with reference to the related drawings. 
     Furthermore, the terms “user,” “subscriber,” “customer,” “consumer” and the like are employed interchangeably throughout, unless context warrants particular distinctions among the terms. It should be appreciated that such terms can refer to human entities or automated components supported through artificial intelligence (e.g., a capacity to make inference based, at least, on complex mathematical formalisms), which can provide simulated vision, sound recognition and so forth. 
     As employed herein, the term “processor” can refer to substantially any computing processing unit or device comprising, but not limited to comprising, single-core processors; single-processors with software multithread execution capability; multi-core processors; multi-core processors with software multithread execution capability; multi-core processors with hardware multithread technology; parallel platforms; and parallel platforms with distributed shared memory. Additionally, a processor can refer to an integrated circuit, an application specific integrated circuit (ASIC), a digital signal processor (DSP), a field programmable gate array (FPGA), a programmable logic controller (PLC), a complex programmable logic device (CPLD), a discrete gate or transistor logic, discrete hardware components or any combination thereof designed to perform the functions described herein. Processors can exploit nano-scale architectures such as, but not limited to, molecular and quantum-dot based transistors, switches and gates, in order to optimize space usage or enhance performance of user equipment. A processor can also be implemented as a combination of computing processing units. 
     As used herein, terms such as “data storage,” data storage,” “database,” and substantially any other information storage component relevant to operation and functionality of a component, refer to “memory components,” or entities embodied in a “memory” or components comprising the memory. It will be appreciated that the memory components or computer-readable storage media, described herein can be either volatile memory or nonvolatile memory or can include both volatile and nonvolatile memory. 
     What has been described above includes mere examples of various embodiments. It is, of course, not possible to describe every conceivable combination of components or methodologies for purposes of describing these examples, but one of ordinary skill in the art can recognize that many further combinations and permutations of the present embodiments are possible. Accordingly, the embodiments disclosed and/or claimed herein are intended to embrace all such alterations, modifications and variations that fall within the spirit and scope of the appended claims. Furthermore, to the extent that the term “includes” is used in either the detailed description or the claims, such term is intended to be inclusive in a manner similar to the term “comprising” as “comprising” is interpreted when employed as a transitional word in a claim. 
     In addition, a flow diagram may include a “start” and/or “continue” indication. The “start” and “continue” indications reflect that the steps presented can optionally be incorporated in or otherwise used in conjunction with other routines. In this context, “start” indicates the beginning of the first step presented and may be preceded by other activities not specifically shown. Further, the “continue” indication reflects that the steps presented may be performed multiple times and/or may be succeeded by other activities not specifically shown. Further, while a flow diagram indicates a particular ordering of steps, other orderings are likewise possible provided that the principles of causality are maintained. 
     As may also be used herein, the term(s) “operably coupled to”, “coupled to”, and/or “coupling” includes direct coupling between items and/or indirect coupling between items via one or more intervening items. Such items and intervening items include, but are not limited to, junctions, communication paths, components, circuit elements, circuits, functional blocks, and/or devices. As an example of indirect coupling, a signal conveyed from a first item to a second item may be modified by one or more intervening items by modifying the form, nature or format of information in a signal, while one or more elements of the information in the signal are nevertheless conveyed in a manner than can be recognized by the second item. In a further example of indirect coupling, an action in a first item can cause a reaction on the second item, as a result of actions and/or reactions in one or more intervening items. 
     Although specific embodiments have been illustrated and described herein, it should be appreciated that any arrangement which achieves the same or similar purpose may be substituted for the embodiments described or shown by the subject disclosure. The subject disclosure is intended to cover any and all adaptations or variations of various embodiments. Combinations of the above embodiments, and other embodiments not specifically described herein, can be used in the subject disclosure. For instance, one or more features from one or more embodiments can be combined with one or more features of one or more other embodiments. In one or more embodiments, features that are positively recited can also be negatively recited and excluded from the embodiment with or without replacement by another structural and/or functional feature. The steps or functions described with respect to the embodiments of the subject disclosure can be performed in any order. The steps or functions described with respect to the embodiments of the subject disclosure can be performed alone or in combination with other steps or functions of the subject disclosure, as well as from other embodiments or from other steps that have not been described in the subject disclosure. Further, more than or less than all of the features described with respect to an embodiment can also be utilized.