Patent Publication Number: US-7583233-B2

Title: RF Receiving and transmitting apparatuses having a microstrip-slot log-periodic antenna

Description:
CROSS-REFERENCE TO RELATED APPLICATIONS 
     This application is a continuation-in-part of application Ser. No. 11/163,119, filed Oct. 5, 2005, now U.S Pat. No. 7,292,197, issued Nov. 6, 2007, which claims the benefit of U. S. Provisional Patent Application Ser. No. 60/617,454, filed Oct. 8, 2004, the disclosures of which are hereby incorporated by reference herein, in their entirety, for all purposes. 
    
    
     BACKGROUND 
     The present invention, in its several embodiments, relates to receiving and transmitting apparatuses that include microstrip log-periodic antennas and, more particularly, to such apparatuses that include microstrip-slot log-periodic antennas. 
     The present practicable range of radio frequency (RF) is approximately 10 kHz to 100 GHz, i.e., 0.01 to 100,000 MHz. Within this frequency range electromagnetic radiation may be detected, typically by an antenna, and amplified as an electric current at the wave frequency. When energized via electric current at an RF wave frequency, an antenna may emit in the RF electromagnetic radiation at the RF wave frequency. Log-periodic antennas are typically characterized as having logarithmic-periodic, electrically conducting, elements that may receive and/or transmit communication signals where the relative dimensions of each dipole antenna element and the spacing between elements are logarithmically related to the frequency range over which the antenna operates. Log-periodic dipole antennas may be fabricated using printed circuit boards where the elements of the antenna are fabricated in, conformal to, or on, a surface layer of an insulating substrate. The antenna elements are typically formed on a common plane of a substrate such that the principal beam axis, or direction of travel for the phase centers for increasing frequency of the antenna, is in the same direction. The antenna elements may be placed in electrical communication with an RF receiver and/or an RF transmitter. The analog and digital processing of the detected RF waveform is typically performed by an RF receiver and the analog and digital processing of the transmitted RF waveform is typically performed by an RF transmitter. 
     SUMMARY OF THE INVENTION 
     The invention in its several embodiments includes radio frequency (RF) receiving and/or transmitting systems or apparatuses having a log-periodic antenna having a dielectric medium such as a printed circuit board interposed between a microstrip log-periodic portion and a proximate slot log-periodic portion. A perimeter of the microstrip log-periodic portion may be undersized relative to a perimeter of a first slot log-periodic antenna portion and a proximate distance between an outer perimeter of the first microstrip log-periodic antenna portion and the perimeter of the first slot log-periodic antenna portion, perpendicular to a second surface may be referenced to bound a first impedance gap. The invention in its several embodiments may further include an antenna having a curvilinear, electrically conductive feed line and a substantially co-extensive curvilinear slot transmission line. Embodiments of the invention may further include an array of two or more log-periodic antennas mounted in alternating phase center orientations. Accordingly, a log-periodic antenna element having a layer of dielectric media interposed between a microstrip log-periodic portion and a slot log-periodic portion may be disposed in an array having two or more like elements that may be placed about vehicles, such as land vehicles, water vehicles and air vehicles, or mounted on stationary structures, such as communication towers. In addition, single or pairs of elements may be mounted to mobile receiving, transmitting, and/or transceiving apparatuses such as vehicles and human-portable interface devices such as mobile telephones and wireless personal data assistants. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       Reference is now made to the following description taken in conjunction with the accompanying drawings, in which: 
         FIG. 1  illustrates in a plan view an example element of a printed circuit and transmission line characteristics of a microstrip line log-periodic array feed side of the present invention; 
         FIG. 2  illustrates in a plan view an example of a ground side of the log-periodic slot array of the present invention; 
         FIG. 3A  illustrates in a plan view an example of six elements in an example array of a microstrip log-periodic feed side of the slot array aligned with a log-periodic ground side of the slot array; 
         FIG. 3B  illustrates in a cross-sectional view an example of an element in the example array of the microstrip log-periodic feed side of the slot array aligned with the log-periodic ground side of the slot array; 
         FIG. 4  illustrates in a plan view an exemplary, typical placement of two antenna elements of the present invention proximate to one another and oriented so that each has a traveling phase center verses frequency opposite the other; 
         FIG. 5A  illustrates in a plan view an exemplary, typical embodiment where a printed circuit board has two microstrip log-periodic array feeds on a top side and their corresponding aligned ground planes on an opposite side of the printed circuit board; 
         FIG. 5B  illustrates in a cross-sectional view a fork region of a tongue of an embodiment engaging a coax inner wire; 
         FIG. 6  illustrates in a cross-sectional view of an exemplary mounting; 
         FIG. 7  illustrates in a plan view of an exemplary curved taper in the grounded side of the exemplary microstrip log-periodic array from the last element to the ground plane; 
         FIG. 8A  illustrates in plan view of an exemplary microstrip feed line as it curves from the feed-line tongue to the base of the exemplary microstrip log-periodic array; 
         FIG. 8B  illustrates in cross-sectional view of an exemplary microstrip feed line as it curves from the feed-line tongue to the base of the exemplary microstrip log-periodic array; 
         FIG. 9  illustrates an exemplary antenna gain pattern produced from measurements of an exemplary antenna taken at a low frequency; 
         FIG. 10  illustrates an exemplary antenna gain pattern produced from measurements taken at a midrange frequency; 
         FIG. 11A  illustrates an exemplary receiver system operably connected to exemplary antenna element embodiments of the present invention; 
         FIG. 11B  illustrates an exemplary transceiver system operably connected to exemplary antenna element embodiments of the present invention; 
         FIG. 12  illustrates an exemplary conformal antenna array disposed about a support structure; 
         FIG. 13  illustrates an exemplary conformal antenna array mounted to portions of an air vehicle; 
         FIG. 14A  illustrates an exemplary system where an array of exemplary antenna elements is disposed about a portion of a communications tower and in communication with mobile apparatuses; and 
         FIG. 14B  illustrates an exemplary arrangement of exemplary antenna elements for integrating with the exemplary mobile apparatuses. 
     
    
    
     As used herein, the term “exemplary” means by way of example and to facilitate the understanding of the reader, and does not indicate any particular preference for a particular element, feature, configuration or sequence. 
     DETAILED DESCRIPTION 
     The present invention, in its several embodiments, include a log-periodic antenna having microstrip slot elements on a first, or top, side of a dielectric medium and a slot ground plane of the elements on a second, or bottom, side of the dielectric medium, where the radiating elements are oriented with alternating and opposing phases, e.g., 180 degrees phase differences, and where the combination may operate as a broadband log-periodic antenna. In addition, the present invention in its several embodiments may have a grounded modified semi-coplanar waveguide-to-microstrip line transition. A feed input of some embodiments typically has a transition from an unbalanced microstrip transmission line and may have a microstrip feed transmission line tapering from a base microstrip slot dipole element on a top side of the dielectric medium and a slotted ground plane under the transmission line tapering from a primary slot dipole element in a ground plane medium on the bottom side of the dielectric medium. Exemplary embodiments of the microstrip transmission line have a primary conductor strip in voltage opposition to a reference ground plane with an interceding dielectric between the two conductors. For example, the element embodiment may be fed by two slot lines in parallel that have as a common potential a main conductor. The main conductor typically tapers to a width that sets an impedance of the microstrip transmission line and along the same length, a void or slot in the ground plane is tapered to a zero width or corner point. In some embodiments, these tapered regions operate to transition the field line from being substantially between the microstrip conductor and the ground plane as in a capacitor, to being substantially fringing fields between the edges of the conductors passing through the dielectric. 
     Exemplary array embodiments of the present invention typically include an array of at least a pair of substantially frequency-independent planar antenna array elements where a first member of the pair of antenna array elements has a phase center axis substantially opposite in direction to the phase center axis of a second member of the pair of antenna array elements. The antenna element patterns may be aligned, i.e., top plan-form relative to bottom plan-form, which forms a microstrip log-periodic array (MSLPA) having a principal axis. Each MSLPA typically includes a slot transmission line running along the principal axis of the MSLPA that may function as feeds for the slot dipole elements the typically trapezoidal elements emanating in bilateral symmetry from the transmission line. In some embodiments, parasitic, or center, microstrip lines or slots may be interposed within the regions formed by the slot dipole elements and the transmission line of the combined layers. The outer perimeter of the feed side of the MSLPA typically describes a pattern or plan-form, the ground plane side of the log-periodic slot array typically then covers a pattern of the perimeter of each feed side microstrip line element of the top side and along with some additional width at substantially perpendicular to the perimeter to establish an impedance slot. 
       FIG. 1  illustrates an exemplary microstrip dipole element array and transmission line characteristics of a microstrip log-periodic array embodiment  100  of the present invention that is typically affixed on a first or top surface  125 , or front side, of a dielectric medium  120 , such as a printed circuit board. The transmission line portion  130  of the exemplary array is within the region subtended by the angle 2β. The log-periodic array of the exemplary embodiment is typically symmetric in a plane about a principal axis  150  where the dipole elements extend as trapezoidal portions bounded, in this example, by the angle 2α. Generally, an internal centered slot  115  is provided by the pattern of the microstrip line at each element and may cross or traverse the transmission line portion  130 . The pattern of a microstrip portion  105  of the MSLPA  100  may be a thin metallic film and the internal centered slot  115  may be fashioned by a trapezoidal region absent of the metallic film. The transverse extent of each interior slot, in this example, is bounded by the angle 2α SL . For purposes of illustrating proportions of the microstrip elements of the antenna, the dipole elements, or dipole teeth of the array that may traverse transmission line portion are numbered starting with the dipole of largest wavelength. For example, a first dipole element  110  is shown with the longest span, i.e., the longest portion traversing the transmission line portion  130 . The exemplary minimal radial distance from the reference origin, O, for the microstrip portion of the first dipole element  110  may be represented as r 1  and the minimal radial distance for the second dipole element may be represented as r 2 . 
       FIG. 2  illustrates an exemplary ground plane side  210  of the microstrip log-periodic slot array (MLPSA)  100  of the present invention where a slot log-periodic antenna portion  200  may be typically formed from a metallic ground plane which may be applied as the bottom or second surface, of an interposed medium, such as a printed circuit board, and may form the back, bottom or opposite side, of the printed circuit board, i.e., opposite the feed side where the microstrip portion  105  of the MLSPA  100  is affixed. A feeder transmission line portion of the array is within the region that may be shown as subtended by the angle 2β plus twice a planar slot width w, shown as a small angle δ, and typically a distance perpendicular to a local perimeter w (not shown in  FIG. 2 ). The slot width is typically adjusted in the matching of the impedance of the array of elements, both the microstrip elements and the slot elements of the ground plane, and including the interposed printed circuit board or other mounting media. Typically, the log-periodic array of the present invention is substantially symmetric in plane about a principal axis  250  where the slot dipole elements traverse a slot transmission line  230  and extend as trapezoids bounded by the angle 2α plus twice the slot width w, represented as a small angle 2δ as above. 
     For purposes of illustrating the slot portions of the slot log-periodic antenna portion  200 , the elements of the array are numbered starting with the slot dipole element of largest wavelength  220 , that is, the element having the exemplary largest transverse span. The maximal radial distance from the reference origin O for the first dipole may be represented as R 1 . The maximal radial distance from the reference origin O for the second dipole may be represented as R 2 . The minimal distance from the reference origin O for the first dipole may be represented as r 1  less the impedance slot width. A similar relationship may be made for radial distances R 2  and r 2 . Typically, the feeder transmission line angle of the microstrip, or top portion is smaller than the angle of 2β plus the angle increment (e.g., 2β), required for impedance slot width of the ground side of the dielectric medium, and likewise the angle 2α bottom plus the angle increments 2β of the ground side required for impedance slot width is greater than 2α of the top side. Rather than expressed by the angle δ, this may be expressed as the linear distance w when viewing the planar projections of the microstrip dipole elements and the slot dipole elements in plan view. 
     For each exemplary pair of top and bottom trapezoidal dipole elements, an impedance slot may be created as shown in the top view of the antenna of  FIG. 3A , where  FIG. 3A  illustrates in a top view an exemplary array of the MSLPA showing six element pairs and where the impedance slot is shown in the space  310  between the microstrip and the ground plane having, in a projection made substantially perpendicular to the local surface and through the interposed dielectric media  120 , the slot width  311 , w. In this exemplary array of the MSLPA, the top and bottom sides are overlaid, where the dashed lines indicate the boundary or slot perimeter of the ground-side present on the bottom side of the dielectric medium. Accordingly, in an exemplary embodiment, the MSLPA is affixed to the dielectric medium, such as a printed circuit board (PCB), in an orientation such that the edges of the ground plane side of the slots of the MLPSA generally provide for an outer perimeter. Put another way, the perimeter of the slot portion is oversized relative to the perimeter of the microstrip portion and the perimeter of the microstrip portion is undersized relative to the slot portion.  FIG. 3B  illustrates in cross-sectional view the microstrip portion  110  of an element in relation to a ground plane portion  210  and an interposed PCB, as an example of a dielectric medium  120 . In this view ( FIG. 3B ), an internal centered slot  115  may be seen in cross-section as well as a slot element  220  of the MLPSA. Also illustrated in cross-sectional view of  FIG. 3B , an impedance slot is shown in the space  310  between the microstrip and the ground plane having, in a planar projection, the slot width  311 , w. The resulting stacked MSLPA is operable to function as a substantially frequency-independent antenna having a traversing of its center with respect to frequency substantially along a line of bilateral symmetry  350  ( FIG. 3A ). 
     Another antenna embodiment is described as follows where w represents the planar width of the impedance slot, τ represents the element expansion ratio, and ∈ represents a measure of tooth width in the following equations: 
     
       
         
           
             
               
                 
                   
                     τ 
                     = 
                     
                       
                         
                           R 
                           
                             n 
                             + 
                             1 
                           
                         
                         
                           R 
                           n 
                         
                       
                       = 
                       
                         
                           r 
                           
                             n 
                             + 
                             1 
                           
                         
                         
                           r 
                           n 
                         
                       
                     
                   
                   ⁢ 
                   
                     
 
                   
                   ⁢ 
                   and 
                 
               
               
                 
                   [ 
                   1 
                   ] 
                 
               
             
             
               
                 
                   ɛ 
                   = 
                   
                     
                       
                         r 
                         n 
                       
                       
                         R 
                         n 
                       
                     
                     . 
                   
                 
               
               
                 
                   [ 
                   2 
                   ] 
                 
               
             
           
         
       
     
     An “over angle” subtended by the completed antenna may be represented 2α+2δ. Exemplary relationships include an ∈ of √{square root over (τ)}, a β of α SL /3, and an α SL  Of (α+δ)/2. 
     Exemplary antenna array properties include a value for the over angle, or 2α+2δ of approximately 36 degrees, a value for 2α of approximately 33 degrees, a value for 2α SL  of approximately 18 degrees, and a value for 2β of approximately 6 degrees. 
     Exemplary antenna array properties are illustrated in Table 1 with distances in inches for dipole teeth numbered 1-19: 
     
       
         
           
               
             
               
                 TABLE 1 
               
             
            
               
                   
               
               
                 Exemplary Antenna Properties 
               
            
           
           
               
               
               
               
               
               
               
            
               
                   
                 R 
                 r 
                 τ 
                 ε 
                 w 
                 # 
               
               
                   
                   
               
            
           
           
               
               
               
               
               
               
               
            
               
                   
                 5.500 
                 4.980 
                 0.82 
                 0.91 
                 0.0866 
                 1 
               
               
                   
                 4.510 
                 4.084 
                 0.82 
                 0.91 
                 0.0710 
                 2 
               
               
                   
                 3.698 
                 3.349 
                 0.82 
                 0.91 
                 0.0582 
                 3 
               
               
                   
                 3.033 
                 2.746 
                 0.82 
                 0.91 
                 0.0477 
                 4 
               
               
                   
                 2.487 
                 2.252 
                 0.82 
                 0.91 
                 0.0391 
                 5 
               
               
                   
                 2.039 
                 1.846 
                 0.82 
                 0.91 
                 0.0321 
                 6 
               
               
                   
                 1.672 
                 1.514 
                 0.82 
                 0.91 
                 0.0263 
                 7 
               
               
                   
                 1.371 
                 1.242 
                 0.82 
                 0.91 
                 0.0216 
                 8 
               
               
                   
                 1.124 
                 1.018 
                 0.82 
                 0.91 
                 0.0177 
                 9 
               
               
                   
                 0.922 
                 0.835 
                 0.82 
                 0.91 
                 0.0145 
                 10 
               
               
                   
                 0.756 
                 0.685 
                 0.82 
                 0.91 
                 0.0119 
                 11 
               
               
                   
                 0.620 
                 0.561 
                 0.82 
                 0.91 
                 0.0098 
                 12 
               
               
                   
                 0.508 
                 0.460 
                 0.82 
                 0.91 
                 0.0080 
                 13 
               
               
                   
                 0.417 
                 0.377 
                 0.82 
                 0.91 
                 0.0066 
                 14 
               
               
                   
                 0.342 
                 0.310 
                 0.82 
                 0.91 
                 0.0065 
                 15 
               
               
                   
                 0.280 
                 0.254 
                 0.82 
                 0.91 
                 0.0053 
                 16 
               
               
                   
                 0.230 
                 0.202 
                 0.77 
                 0.88 
                 0.0047 
                 17 
               
               
                   
                 0.177 
                 0.155 
                 0.77 
                 0.88 
                 0.0036 
                 18 
               
               
                   
                 0.136 
                 0.120 
                 0.77 
                 0.88 
                 0.0028 
                 19 
               
               
                   
                   
               
            
           
         
       
     
     The present invention, in its several embodiments, typically has the antenna structurally divided into two portions on either side of a mounting medium, such as a two-sided PCB. The two-sided printed circuit board embodiment accommodates an exemplary feed described below. That is, a feed transition from a microstrip to radiating elements may be fabricated with a dielectric medium, such as a two-sided printed circuit board and a tapered ground. In addition to the various feed embodiments, the two-sided PCB structure and material provide additional means by which the antenna impedance of the several antenna embodiments may be controlled, for example, by variation of material thickness and by selection of a dielectric constant of the PCB. Due to a field constraint within the dielectric material, high power, high frequency alternative embodiments of the present invention may exploit the increased breakdown characteristics of the higher frequency, i.e., the smaller wavelength, portion of the antennas. 
       FIG. 4  illustrates an exemplary placement of two microstrip, log-periodic arrays of an embodiment of the present invention that are proximate to one another and oriented so that a phase center  415  of a first antenna  410  is substantially opposite a phase center  425  of a second antenna  420  and may receive or transmit substantially as a single combined antenna element. These opposing phase centers are typically offset, which may adapt these combined elements to the direction finding of targets out of the plane of the elements; that is, receiving RF energy at angles of arrival substantially off the axes of the opposing phase centers  415  and  425 . 
       FIG. 5A  illustrates an exemplary embodiment  500  where a PCB has two MSLPAs with feeds on an illustrated upper surface, or top side, and corresponding aligned ground planes on an opposite surface, or bottom side, of the PCB where each form an antenna and together form an antenna array on the PCB.  FIG. 5A  illustrates exemplary feed tongues  510  and a second feed tongue  520 , i.e., one for each antenna. For example, an inner wire or conductor  523  of a coaxial feed line, once within a fork  511  or  521  of each feed tongue, may be soldered or otherwise put in electrical connectivity with a microstrip feed line  512 ,  522  and soldered or otherwise put in electrical connectivity with the ground plane. As illustrated by  FIG. 5B , a cross-sectional view of  FIG. 5A  at the second feed tongue  520 , typically, an outer conductor  524  of a coaxial conductor may also have direct current (DC) connectivity with the ground plane  210 , which is shown by example as being on the bottom side of the PCB  120 , and the inner wire  523  also typically has connectivity with the microstrip feed line  522  which is shown by example as being on the top side of the PCB  120 . Further detail of the planar projection of the perimeter of an exemplary curvilinear portion of the microstrip feed line relative to the planar projection of the perimeter of an exemplary curvilinear, tapered ground transition is described below and illustrated in  FIG. 8A . 
     Mounting 
     The antenna array elements of the several embodiments may be mounted above a grounded cavity, or other receiving element, which provides both grounding and feed lines such as the coaxial conductor example described above. Illustrated in  FIG. 6  is an exemplary cavity having a bottom surface  610  that may be formed of metal, e.g., steel, titanium, aluminum or various metal alloys, where a radio frequency absorber element  620 , or sheet, may be interposed between the cavity surface and the bottom side such as the ground plane  210  of the antenna array elements. In addition, a low dielectric material deployed as foam or a honeycomb-type element  630  that may be interposed between the radio frequency absorber element  620  and the bottom side  210  of the antenna array elements. 
     The antenna array element  100 , the radio frequency absorber element  620 , and a low dielectric element may be bonded together. For environmentally challenging environments, such as for example those encountered in moisture laden atmosphere with high dynamic pressures experienced at supersonic velocities, a cover  640 , skin, or radome may be used to shield, or protect, or otherwise cover all or a portion of the top surface  125  or outwardly directed portion of the antenna array element, a covered portion that may include the top side  125  of the dielectric medium  120 , thereby covering a region that could or would otherwise be in direct environmental contact with free space, for example. The microstrip line array of the top side  125  and the ground plane slots of the bottom side of the array may be fabricated on a low loss, low dielectric substrate, e.g., RT5880 DUROID®, a substrate available from Rogers Corporation, Advanced Circuit Materials Division, of Chandler, Ariz., or may be fabricated of equivalently low dielectric materials at thickness of around 15 mils, for example. Other thickness ranges may be used depending on the properties of the low dielectric material and a desired gap  310  ( FIG. 3B ). In addition, a cavity resonance absorber, such as a flexible, ferrite-loaded, electrically non-conductive silicone sheet may be applied within a cavity mounting. Where the cavity is formed of metal or has a metalized or electrically conductive surface, the antenna array may be in electrical contact with the cavity surface where the cavity surface may serve as the base ground plane of the antenna array. In addition, the two-sided PCB embodiments of the array may provide the ability to control, by selection, the impedance by selecting from variations of PCB material thickness and their respective dielectric constants. 
     The substantially planar profile of the antenna array may exhibit some curvature and, whether flat or contoured, may be conformally mounted. In those geometries requiring conformal mounting about a radius of curvature, the transverse edges of the otherwise typically trapezoidal dipole elements are themselves typically curved to accommodate a curved printed circuit board surface that may then conform to a selected mounting geometry. 
     The several embodiments of the invention have gain and pattern properties, which are typically robust with respect to an effect of cavity depth on the elements. For example, a cavity with an absorber-lined bottom surface and metal back negligibly affects on the antenna gain and pattern properties where cavity depth is at a minimum of 0.1 lambda, i.e., one-tenth of a wavelength of the frequency in question. Put another way, the exemplary embodiments may be configured to experience a slight loss of antenna gain or antenna gain-angle pattern distortion for cavities shorter than one-tenth lambda with a corresponding change in the input voltage standing wave ratio (VSWR). 
     Microstrip Feed Structure 
     Some high power, high frequency applications of the several embodiments may experience an increase in the breakdown characteristics of the high frequency portion of the elements. Exemplary feed structure embodiments readily accommodate elements operating from frequencies below X-band through well into the Ka-band. In order to accommodate structures into the upper Ka-band, micro-etching techniques are typically applied. At these higher frequencies, material thicknesses are typically reduced from those accommodating X-band antenna embodiments. 
     Each of the antenna array elements typically includes a microstrip feed structure that splits and feeds to the two-sided antenna array element. Some embodiments of the feed structure combine microstrip feed lines with a tapered ground transition and the two-sided antenna element. Typically the feed structure includes a microstrip feed line having a tapered ground transition.  FIG. 7  illustrates an exemplary curvilinear, tapered ground transition  710  from the last element (e.g., a high or highest frequency element) of the MSLPA. A transition from the last slot element  720  to a feed transmission line is tapered in this exemplary fashion in part to minimize VSWR effects and to continue the transition from microstrip to the antenna element. The feed transmission line is tapered in this exemplary embodiment to a point  740 . In addition, a base of a slot feed transmission line taper may curve in a direction of the exemplary feed-line tongue  510 ,  520  (not depicted) to minimize sharp angles that may otherwise set up what may be undesired or parasitic active portions. 
       FIG. 8A  illustrates an exemplary microstrip feed line  810  as it curves from the feed line tongue  510  (see  FIG. 5A ) to the base of the MSLPA  820  where the feed line  810  flares out to a last element of the MSLPA. A last element  830  of the MSLPA is tapered, in this example, in part to minimize feed point radiation and prevent the last element from arraying with the proximate element to form a radiating beam for this section and accordingly improve input matching over base elements lacking a tapered feed line. The tapering, or decreasing width, of the transition from the last slot element  720  to the slot feed transmission line  710  may cause the slot width or perimeter of the slot feed transmission line, in a planar projection made perpendicular or substantially perpendicular to the surface or local surface regions of the dielectric medium  120  to which the slotted ground plane  210  is attached, to fall within, as depicted at  850 , the plan form of the exemplary microstrip feed line  810  that is to be within a projection of the perimeter of the microstrip feed line  810  made perpendicular to the surface or local surface regions of the dielectric medium  120  to which the microstrip feed line  810  is attached. The last element in these exemplary embodiments typically does not have a parasitic slot within its perimeter. Also shown in this view is the relative orientation of the exemplary microstrip feed line  810  and the curvilinear, tapered ground transition  710  along with its exemplary tip ending  740  that, in a planar projection made planar to the local surface, is within the plan form, or perimeter, of the exemplary microstrip feed line  810 ; that is, within a projection of the exemplary microstrip feed line  810  made perpendicular to the local surface. Accordingly, when viewed in plan view and projecting across the interposed dielectric medium  120 , the antenna embodiments may have a curvilinear, electrically conductive microstrip feed line  810  and a substantially co-extensive curvilinear slot transmission line  710  for a portion of the run of the microstrip feed line  810 .  FIG. 8B  illustrates in cross-sectional view, the exemplary microstrip feed line  810  as it curves from the feed line tongue  510  to the base  820  of the MSLPA where the feed line flares out to the last element  830  of the MSLPA. Also illustrated in this view is the tapered ground transition  710  ending at the tip corner  840 . 
     Receiving, Transmitting and Transceiving 
     The antenna array embodiments of the present invention may provide substantially constant forward directivity, typically with only subtle or otherwise operationally negligible changes in beam-width, and afford an antenna array of forward and aft facing elements of equal or nearly equal performance. For purposes of illustrating the performance of an embodiment of the present invention, the antenna array of forward-oriented and aft-oriented element arrays where the MSLPAs have fifteen trapezoidal dipole elements, i.e., teeth, and one base tapered trapezoidal dipole element were tested.  FIG. 9  illustrates an antenna gain pattern  900 , in dB, as a function of beam angle pattern produced from measurements taken at a low frequency, i.e., directed radio frequencies intended to excite the larger dipole elements.  FIG. 10  illustrates an antenna gain pattern  1000 , in dB, as a function of beam angle produced from measurements taken at a midrange frequency, i.e., directed radio frequencies intended to excite the intermediate-sized dipole elements. 
     The antenna pairs  500  ( FIG. 5A ) may be mounted, as arrays of pairs, to surfaces that may include surfaces integral to vehicles, such as air vehicles and surface portions of sensor pods that may be deployed on vehicles such, as air vehicles. 
     The antenna element embodiments are suitable for conformal mounting, for example, structures shaped principally for low drag properties such as those shapes found in air vehicles and land and marine vehicles having application sensitive to dynamic pressure conditions and disruptions of laminar flow patterns. Accordingly, an exemplary mounting site for one or more antenna elements may be a portion of a rocket or missile. The cylindrical shape of the body would allow for a circumferential array of elements of fore and aft configuration. With excellent low angle pattern coverage the system could achieve near full hemispheric coverage. Such a system can provide direction finding (DF) and angle-of-arrival (AOA) input signals. For some broad side angles it also provides additional benefit in AOA and DF in that there are twice as many elements with opposing phase directions that have a view of the incoming signal. A single forward looking set may be implemented for a forward-only array for DF/AOA applications. A single forward looking set would simply have limited the total field of view compared with a forward and rear-looking embodiment. 
     The antenna elements may be electrically connected to a radio frequency receiver system or a radio frequency transmitting and receiving system which may be termed a transceiver. An RF receiver may process the electric current from the antennas via a low noise amplifier (LNA) and may then down convert the frequency of the waveform via a local oscillator and mixer and may process the resulting intermediate frequency waveform via an adaptive gain control amplifier circuit. The resulting conditioned waveform may be sampled via an analog-to-digital converter (ADC) with the discrete waveform being processed via a digital signal processing module. Where the frequency of the RF waveform is well within the sampling frequency of the conversion rate of the ADC, direct conversion may be employed and the discrete waveform may be processed at a rate comparable to the ADC rate. Receivers may further include signal processing and/or control logic via digital processing modules having a microprocessor, addressable memory, and machine executable instructions. An RF transmitter may process digital waveforms that have been converted to analog waveforms via a digital-to-analog converter (DAC) and may up-convert the analog waveform via an in-phase/quadrature (I/Q) modulator and/or step up the waveform frequency via a local oscillator and mixer, then amplify the up-converted waveform via a high-power amplifier (HPA) and conduct the amplified waveform as electric current to the antenna. Transmitters may further include signal processing and/or control logic via digital processing modules having a microprocessor, addressable memory, and machine executable instructions. Transceivers generally have the functionality of both a receiver and a transmitter, typically share a component or an analog or digital signal processing module, and employ signal processing and/or control logic via digital processing modules having a microprocessor, addressable memory, and machine executable instructions. 
       FIG. 11A  illustrates in a functional block diagram that as part of a receiver system  1100 , the RF energy sensed by the exemplary antenna elements  1111 ,  1112  of an antenna array  1110  may be processed within a receiver subsystem  1101  via switches, low noise amplifiers, bandpass filters and/or other signal conditioning processes and filters and may be stepped down, i.e., down converted, in frequency for further processing by the digital signal processing  1102  of the receiver and associated digital signal processing.  FIG. 11B  illustrates in a functional block diagram that as part of a transceiver system  1150  having an RF receiving, or receiver, subsystem  1151  and an RF transmitting, or transceiver, subsystem  1155 , the exemplary antenna elements  1161 ,  1162  of an antenna array  1160  may be energized, via one or more properly thrown switches  1153  to transmit signals initiated by the digital signal processing  1154  and conditioned by a transmitting subsystem  1155  and, when not transmitting, the exemplary antenna elements  1161 ,  1162  may function as passive elements to sense incoming RF energy that this is conducted, again via one or more properly thrown switches  1153  to the RF receiver system  1151 . An RF transmitting system, whether a transceiver subsystem or a separate transmitter system, functions separately at the front-end (i.e., proximate to the antennas) from the receiver and so the transmitter antennas and receiver antennas may be physically different antennas or time-shared via switches. Accordingly, references to an RF transmitter refer generally to the transmitting functionality whether embodied as a stand-alone transmitter or a transmitter subsystem of a transceiver. Likewise, references to an RF receiver refer generally to the receiving functionality whether embodied as a stand-alone receiver or a receiver subsystem of a transceiver. 
       FIG. 12  illustrates an array of antenna pairs  1210 , where each pair  500  has an alternating forward-directed phase center  415  and aft-directed phase center  425 , and each pair  500  is disposed substantially equidistantly about a centerline  1220  of a mounting structure  1200 , itself having a surface  1205  that may form a portion of the fuselage or other surface of an air vehicle. 
     While cylindrical or round embodiments of an array of antenna elements or pairs of elements have been shown in the example of an air vehicle fuselage, these elements, of one or various scales, may be applied to oval, rectangular and multisided structures, such as hexagons and octagons. Antenna elements, of one or various scales, may also be embedded into surfaces of wings along an axis rather than or in addition to an array disposed circumferentially about the fuselage. Multiple elements can be separated by a wing or fuselage, exemplified by separation on the top and bottom of a wing or on the left and right wings, or on the vertical fins of an aircraft or missile.  FIG. 13  illustrates the mounting structure  1200  placed at a forward end of a fuselage  1310  and, in this example, placed aft of a nose cone or radome  1320 . The mounting structure has an array of antenna pairs  1110 , placed at a front end of an exemplary air vehicle  1300  which may then cooperatively function as a mobile receiving or transmitting apparatus. The array of antenna pairs  1210  is typically covered by a protective covering  640  when the mounting structure is placed in proximity to the front end of the air vehicle  1300 . The front end portion of the fuselage  1310  having an MSLPA  100  ( FIG. 3A ), an antenna pair  500 , or an array of antenna pairs  1210  may comprise a guidance section  1330  of the air vehicle  1300 . The guidance section  1330  may further include the nose cone or radome  1320 . Also shown is a linear array of antenna pairs  1350  mounted conformally on a lifting surface  1360  of the air vehicle  1300 . 
     Some antenna embodiments of the present invention may be used to send, receive or transceiver RF signals. Accordingly, an array of at least a pair of substantially frequency independent planar antenna array elements may function as a receiving array and may alternatively function as a transmitting array or a transmitting and receiving, that is, the array may function as a transceiver array. 
     Scaled Embodiments 
     Because of the feed structure, the bandwidth capabilities are extremely broad. A scaled version of the prototype antenna was created at one-seventh ( 1/7) of the original size. Properties of an exemplary antenna scaled from the example antenna of Table 1 are provided in Table 2 with distances in inches for dipole teeth numbered 1-9: 
     
       
         
           
               
             
               
                 TABLE 2 
               
             
            
               
                   
               
               
                 Exemplary Antenna Properties 
               
            
           
           
               
               
               
               
               
               
               
            
               
                   
                 R 
                 r 
                 τ 
                 ε 
                 w 
                 # 
               
               
                   
                   
               
               
                   
                 0.756 
                 0.685 
                 0.82 
                 0.91 
                 0.0119 
                 1 
               
               
                   
                 0.620 
                 0.561 
                 0.82 
                 0.91 
                 0.0098 
                 2 
               
               
                   
                 0.508 
                 0.460 
                 0.82 
                 0.91 
                 0.0080 
                 3 
               
               
                   
                 0.417 
                 0.377 
                 0.82 
                 0.91 
                 0.0066 
                 4 
               
               
                   
                 0.342 
                 0.310 
                 0.82 
                 0.91 
                 0.0065 
                 5 
               
               
                   
                 0.280 
                 0.254 
                 0.82 
                 0.91 
                 0.0053 
                 6 
               
               
                   
                 0.230 
                 0.208 
                 0.82 
                 0.91 
                 0.0036 
                 7 
               
               
                   
                 0.188 
                 0.171 
                 0.82 
                 0.91 
                 0.0030 
                 8 
               
               
                   
                 0.155 
                 0.140 
                 0.82 
                 0.91 
                 0.0024 
                 9 
               
               
                   
                   
               
            
           
         
       
     
     Dielectric thickness was also partially scaled down from the antenna element characterized in Table 1, but, due to material limitations, was not fully scaled down. The one-seventh scaled antenna element characterized by Table 2 has only one-quarter (¼), rather than a one-seventh, of the dielectric thickness of the antenna element characterized in Table 1. So, if RT5880 DUROID® is used as a substrate, the scaled thickness of the antenna element characterized in Table 2 is approximately 4 mils. Overall, the scaling resulted in the antenna element characterized in part by Table 2 operating at seven times the frequency of the antenna characterized in part by Table 1, and the scaled antenna element was tested to the frequency limit of the network analyzers supporting the test conditions. The feed structure continued to operate to the analyzer upper limit which is more than double the frequency of the full scale element example of Table 1. Being readily scalable, the various scaled embodiments of the exemplary antenna may be applied to a variety of structures due in part to their functioning at the various scaled sizes. 
     In telecommunication applications, the extreme bandwidth and opposing phase travel of pairs of elements support systems such as cellular base stations or point-to-point communication systems. Typical cellular system frequencies range from 800 MHz to 2 GHz in the United States, or as high as 3.4 GHz abroad. This extreme bandwidth provides a diversity antenna system to allow switching to the strongest signal and yet provide attenuation to other towers limiting tower interference and reducing tower traffic. From a mobile unit side, an antenna element, pair of elements, or array of elements or array of elements pairs may be conformally mounted into the top surface of a vehicle such as a car or truck. One antenna could allow for coverage of all cellular systems in a single element. From the tower side, an annular or circular-shaped array may provide DF/AOA tracking of subscribers for system traffic control or to enhance E911 capabilities of the overall system. Exemplary telecommunication embodiments may exhibit particular applicability when considering phones or communication appliances that do not include a GPS tracking capability or where the GPS quality is attenuated due to partial or complete satellite line-of-sight blockage.  FIG. 14A  illustrates a mobile communication system  1400  comprising a communication tower  1402 , a handset  1404  (for example, a human-portable user communication interface), having, for example, one or a pair of conformally embedded exemplary antenna elements  1430  (not shown) and a transceiver, and the system may further comprise a vehicle  1406  also having a pair of exemplary antenna elements  1430  and a transceiver (not shown). The mobile communication system  1400  may further comprise a mobile communications platform functioning similarly to the stationary communications tower  1402  and may further include air vehicles  1300  (see  FIG. 13 ). The handset  1404  may include a human auditory interface for speaking and listening and may include a visual and/or tactile interface for textual and/or graphic communications. The communication tower  1402 , as a stationary receiving or transceiving apparatus, comprises an antenna array  1410  of antenna element pairs  1420 , that may be disposed at a distal end  1405  of a tower or mast  1403 , i.e., above the ground anchor points, where the first antenna element  1421  is electrically oriented in a direction opposite a second element  1422 . An antenna element pair site  1430  for the mobile receiving apparatuses may be manufactured into or made substantially conformal with for example a roof portion of a vehicle  1406  or a panel portion of the handset  1404 . The handset  1404  is an example of a human-portable interface unit having a transceiver and one or more antenna elements that is in a range of mass portable by a human that includes masses that may be hand-held and masses that may be carried via a backpack or similar conveyance. The exemplary antenna pair site  1430  may include a mounting medium  1440  and at least a first antenna element  1441  and where dimensional applications allow, a second antenna element  1442 . In some embodiments, a mobile receiving device  1300  (see  FIG. 13 ),  1404 ,  1406 , or apparatus, may be switched to a mobile transmitting device and its transmissions received by a second mobile receiving device or apparatus. 
     The configuration of the exemplary embodiments of the antenna element structure allows for adaptation to a variety of media and/or materials. For example, materials for manufacture may range from low cost commercial dielectrics to materials known to endure extreme temperature condition for any and all applications. Low cost commercial materials such as foams or plastics of proper thicknesses, i.e., thickness sufficient to provide the electric separation of portions and the electromagnetic interaction of the portions as provided by the exemplary dielectric of 15 mil and 4 mil thicknesses, may allow for very inexpensive embodiments to be mass produced for commercial hand sets or automotive applications. Midrange materials, such as Rogers 4003, may be used for higher performance, low cost, applications which require little conformity. More flexible materials such as polytetrafluoroethylene (PTFE) circuit materials can be used for high performance mid to high temperature applications such as high speed aircraft which may also require contour matching of the air vehicle skin. Extreme conditions, such as space vehicles or very high speed air vehicles, can take advantage of layered ceramic materials and ceramet or palladium silver, as examples of fired metalized coatings, which can withstand temperatures in excess of 750 degrees Fahrenheit. 
     Many alterations and modifications may be made by those having ordinary skill in the art without departing from the spirit and scope of the invention. Therefore, it must be understood that the illustrated embodiments have been set forth only for the purposes of example and that it should not be taken as limiting the invention as defined by the following claims.