Patent Publication Number: US-6667652-B2

Title: Stabilized power circuit

Description:
FIELD OF THE INVENTION 
     The present invention relates to a dropper-type stabilized power circuit, and specifically to a configuration which prevents a reverse current which flows from the output side to the input side in a low-saturation-type stabilized power circuit which utilizes a PNP-type transistor. 
     BACKGROUND OF THE INVENTION 
     FIG. 15 shows a basic structure of a low-saturation-type series regulator  51 , one of dropper-type stabilized power circuits, which utilizes a PNP-type transistor as a power transistor. 
     An emitter of a power transistor  11  is connected to an input terminal IN of the series regulator  51 . Further, a collector of the power transistor  11  is connected to an output OUT of the series regulator  51 . 
     A collector of a driving transistor  12  made up of an NPN-type transistor is connected to a base of the power transistor  11 . Further, an emitter of the driving transistor  12  is connected to a GND. 
     An output terminal of an error amplifier  13  is connected to a base of the driving transistor  12 . Further, an inverting input terminal of the error amplifier  13  is connected to a junction of a voltage dividing resistance R 1  and a voltage dividing resistance R 2  which are provided in series between the output terminal OUT of the series regulator  51  and the GND. 
     A non-inverting input terminal of the error amplifier  13  is connected to a standard power circuit  14  which generates a reference voltage Vref 1 . Further, a power voltage Vcc of the error amplifier  13  and the standard power circuit  14  is taken from the input side of the series regulator  51 . Further, a high-temperature-leak compensating resistance R EB  is provided between the emitter and the base of the power transistor  11 . 
     In the foregoing structure, a feedback voltage corresponding to an output voltage Vo which exists from the junction of the voltage dividing resistances R 1  and R 2  to the series regulator  51  is inputted to the error amplifier  13 . Further, the error amplifier  13  compares the feedback voltage with the reference voltage Vref 1  of the standard power circuit  14  and outputs a voltage according to the gap between the feedback voltage and the reference voltage Vref 1 , so that the error amplifier  13  adjusts a collector current of the driving transistor  12 , that is, a base current of the power transistor  11 . This adjustment increases/decreases the collector current of the power transistor  11 , so that the output voltage Vo is stabilized. 
     The high-temperature-leak compensating resistance R EB  increases the collector current of the power transistor  11  by increasing a leak current of the driving transistor  12  at high temperatures, so that a rise of the output voltage Vo is prevented. 
     However, in the conventional dropper-type stabilized power circuit such as the foregoing series regulator  51  which utilizes the high-temperature-leak compensating resistance R EB , there is a case where a voltage higher than input voltage (Vin) is applied to the output (OUT) of the stabilized power circuit from outside due to a misconnection etc. In this case, a base current in a reverse direction flows from the output side via the collector of the power transistor ( 11 ), the base of the power transistor ( 11 ), and the high-temperature-leak compensating resistance R EB  to the input side. Thus, the power transistor ( 11 ) becomes ON in a reverse direction, so that there exists a problem that the reverse current flows from the output side to the input side. 
     Japanese Unexamined Patent Publication No. 36711/1993 (Tokukaihei 5-36711) (published date: Feb. 12, 1993) discloses a following stabilized power circuit. In the stabilized power circuit, a diode is provided in parallel with a power transistor so that an output side is an anode and an input side is a cathode. Thus, the reverse current flows to the diode, so that the power transistor is protected. 
     However, for example, in a portable device which utilizes a battery, there is a case where it is possible to obtain an output of the stabilized power circuit from a body via a connection terminal such as an option. In this case, there is a possibility that a voltage higher than an input voltage (Vin) can be applied to the output (OUT) of the stabilized power circuit due to a misconnection etc. In such a case, since input of the stabilized power circuit is supplied by a battery, the battery is charged by the reverse current. Further, there is a possibility that the battery may ignite due to overcharge, depending on cases. Thus, even when the series regulator  51  which is arranged to have the high-temperature-leak compensating resistance R EB  has a diode for a by-puss like the foregoing publication, this problem cannot be solved. 
     SUMMARY OF THE INVENTION 
     The object of the present invention is to provide a dropper-type stabilized power circuit which can prevent a reverse current which flows from an output side to an input side, even when a voltage of an output side is higher than voltage of an input side with a high-temperature-leak compensating resistance provided. 
     The dropper-type stabilized power circuit of the present invention, in order to achieve the foregoing object, includes a PNP-type transistor; a high-temperature-leak compensating resistance provided between an emitter and a base of the power transistor; a compensating resistance switch provided in series with the high-temperature-leak compensating resistance between the emitter and the base; an output terminal which outputs a voltage; an input terminal to which a voltage is inputted; and compensating resistance switch controlling means for detecting a voltage of the output terminal and conducting the compensating resistance switch under normal operating conditions in which an input voltage of the input terminal is dropped so as to obtain an output voltage of the output terminal, and not conducting the compensating resistance switch when the detected output voltage is higher than the output voltage under normal operating conditions and is not less than a predetermined value which is set to be not more than value at which a current begins to flow from a collector to the base of the power transistor. 
     According to the invention, under normal operating conditions in which the input voltage is dropped so as to obtain the output voltage, the compensating resistance switch controlling means conducts a compensating resistance switch provided in series with the high-temperature-leak compensating resistance between the emitter and the base of the power transistor, and makes the high-temperature-leak compensating resistance ready to function. On the other hand, when a voltage of the output terminal becomes higher than the output voltage under normal operating conditions due to miss-connection etc. and becomes higher than the predetermined value which was set to be not more than a value at which a current begins to flow from the collector to the base of the power transistor, the compensating resistance switch controlling means does not conduct the compensating resistance switch so that a current does not flow to the high-temperature-leak compensating resistance. 
     Thus, even when a voltage of the output terminal is not less than the value at which a current begins to flow from the collector to the emitter of the power transistor, there is no current which flows from the collector via the base of the power transistor to the high-temperature-leak compensating resistance. Further, when the output voltage becomes high in a dropper-type stabilized power circuit, a base current of the power transistor is restrained generally, so that a base current of the power transistor is controlled so as not to flow under abnormal operating conditions in which a voltage of the output terminal is higher than a voltage of the input terminal. Thus, under abnormal operating conditions, the current which flows from the collector via the base of the power transistor to the paths other than the high-temperature-leak compensating resistance is restrained. By this, it is possible to prevent the power transistor from being ON in a reverse direction. 
     As a result, it is possible to provide the dropper-type stabilized power circuit which can prevent the reverse current which flows from the output side to the input side, when voltage of the output side is higher than voltage of the input side with the high-temperature-leak compensating resistance provided, For a fuller understanding of the nature and advantages of the invention, reference should be made to the ensuing detailed description taken in conjunction with the accompanying drawings. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is a circuit block diagram showing a structure of a stabilized power circuit according to the first embodiment of the present invention. 
     FIG. 2 is a circuit block diagram showing a more specific structure of the stabilized power circuit of FIG.  1 . 
     FIG. 3 is a circuit block diagram showing a structure of a modified example of the stabilized power circuit of FIG.  1 . 
     FIG. 4 is a circuit block diagram showing a structure of a stabilized power circuit according to the second embodiment of the present invention. 
     FIG. 5 is a circuit block diagram showing a more specific structure of the stabilized power circuit of FIG.  4 . 
     FIG. 6 is a circuit block diagram showing a structure of a modification example of the stabilized power circuit of FIG.  4 . 
     FIG. 7 is a circuit bock diagram showing a structure of a stabilized power circuit according to the third embodiment of the present invention. 
     FIG. 8 is a circuit block diagram showing the first structure of the stabilized power circuit which is more specific than FIG.  7 . 
     FIG. 9 is a circuit block diagram showing the second structure of the stabilized power circuit which is more specific than FIG.  7 . 
     FIG. 10 is a circuit block diagram showing the third structure of the stabilized power circuit which is more specific than FIG.  7 . 
     FIG. 11 is a circuit block diagram showing the first structure of a stabilized power circuit according to the fourth embodiment of the present invention. 
     FIG. 12 is a circuit block diagram showing the second structure of the stabilized power circuit according to the fourth embodiment of the present invention. 
     FIG. 13 is a circuit block diagram showing a structure of a stabilized power circuit according to the fifth embodiment of the present invention. 
     FIG. 14 is a circuit block diagram showing a structure of a stabilized power circuit according to the sixth embodiment of the present invention. 
     FIG. 15 is a circuit block diagram showing a structure of a conventional stabilized power circuit. 
    
    
     DESCRIPTION OF THE EMBODIMENTS 
     [First Embodiment] 
     One embodiment which realizes a stabilized power circuit of the present invention is described by using FIG. 1 to FIG. 3 as follows. Note that, components which have the same functions as components described in the foregoing BACKGROUND OF THE INVENTION are given same reference numerals, and descriptions thereof are omitted. 
     FIG. 1 shows a structure of a series regulator  1  as a stabilized power circuit according to the present embodiment. 
     The series regulator  1  includes a power transistor  11 , a driving transistor  12 , an error amplifier  13 , a reference voltage circuit  14 , an output voltage detecting circuit  15 , a switch driving circuit  16 , voltage dividing resistances R 1  and R 2 , a high-temperature-leak compensating resistance R EB , and a compensating resistance switch SW 1 . 
     The compensating resistance switch SW 1  is provided between an emitter and a base of the power transistor  11  in series with the high-temperature-leak compensating resistance R EB . Further, when the compensating resistance switch SWI is conducted, it makes up a current path including the high-temperature-leak compensating resistance R EB , and when the compensating resistance switch SW 1  is not conducted, it separates the high-temperature-leak compensating resistance R EB  from an emitter/base line. 
     The output voltage detecting circuit  15  detects voltage of an output terminal OUT. Further, this output voltage detecting circuit  15  detects a stabilized output voltage Vo when the series regulator  1  which obtains the output voltage Vo by dropping an input voltage Vin under normal operating conditions. Further, when a voltage is applied to the output terminal OUT from outside, the output voltage detecting circuit  15  detects a total output voltage Vo including the applied voltage. Further, the detected result is inputted to a switch driving circuit  16 . 
     The switch driving circuit  16  compares a voltage of predetermined value which was generated therein or given from outside with the output voltage Vo detected by the output voltage detecting circuit  15 . Further, the switch driving circuit  16  outputs a controlling signal which opens or closes the compensating resistance switch SW 1  according to whether the output voltage Vo is higher than the predetermined value or not. The predetermined value is used to judge whether or not the output voltage Vo has become higher than the value under normal operating conditions to approach to the state that the reverse current flows from an output side of the series regulator to an input side. 
     In a case where the compensating resistance switch SW 1  is conducted, the reverse current begins to flow from the output side to the input side when the output voltage Vo is higher than the input voltage Vin by not less than the inverse voltage (about 0.7V) between the collector and the base in the power transistor  11 . 
     Thus, the predetermined value which is higher/lower comparing standard of the output voltage Vo is set to be higher than the output voltage Vo under normal operating conditions (normal value), and is set to be not more than the output voltage Vo (normal value) +0.7 V which is exactly lower than the value at which the inverse current begins to flow. Further, when the predetermined value is set to be near the output voltage Vo (normal value), there is a fear that the high-temperature-leak compensating resistance R EB  is separated even under normal operating conditions due to the change of temperature of the output voltage Vo etc. Taking this into consideration, it is preferable that the predetermined value is set to be within a range from the output voltage Vo (normal value) +0.5V to the output voltage Vo (normal value) +0.7V. 
     That is, the predetermined value is set to be higher than the output voltage Vo under normal operating conditions, and to be lower than the value at which a current begins to flow from the collector to the base of the power transistor  11 . Under normal operating conditions, the output voltage Vo is lower than the predetermined value, and the switch driving circuit  16  outputs a signal for conducting the compensating resistance switch SW 1 . While, when the output voltage Vo is higher than the predetermined value, the switch driving circuit  16  outputs a controlling signal which makes the compensating resistance switch SW 1  nonconductive. 
     Thus, the output voltage detecting circuit  15  and the switch driving circuit  16  detect the voltage of the output terminal OUT of the series regulator  1  under normal operating conditions, and conduct the compensating resistance switch SW 1 . While, when the voltage is higher than the output voltage Vo under normal operating conditions and higher than the predetermined value set to be lower than the value at which a current begins to flow from the collector to the base of the power transistor  11 , the output voltage detecting circuit  15  and the switch driving circuit  16  include compensating resistance switch controlling means which makes the compensating resistance switch SW 1  non-conductive. 
     In this way, the compensating resistance switch SW 1  is conducted by the compensating resistance switch controlling means, and the high-temperature-leak compensating resistance R EB  becomes ready to function under normal operating conditions. While, in a case where the voltage of the output terminal OUT becomes higher than the predetermined value due to misconnection etc., the compensating resistance switch SW 1  is made nonconductive by the compensating resistance switch controlling means so that a current does not flow to the high-temperature-leak compensating resistance R EB . 
     Thus, even when a voltage of the output terminal OUT is higher than the value at which a current begins to flow from the collector to the base of the power transistor  11 , there is no current which flows from the collector via the base of the power transistor  11  to the high-temperature-leak compensating resistance R EB . Further, when the voltage of the output terminal OUT is higher than the output voltage Vo under normal operating conditions in FIG. 1, the driving transistor  12  is controlled so as to be OFF. 
     That is, when the output voltage becomes high, the dropper-type stabilized power circuit suppresses a base current of the power transistor generally. Therefore, under abnormal operating conditions in which the voltage of the output terminal is higher than the input voltage, the base current of the power transistor can be controlled so as not to flow. Thus, under abnormal operating conditions, it is possible to suppresses the current which flows from the collector via the base of the power transistor to paths other than the high-temperature-leak compensating resistance R EB . In this way, it is possible to prevent the power transistor from being ON in a reverse direction. 
     As a result, even when the voltage of the output side is higher than the input voltage with the high-temperature-leak compensating resistance R EB  provided, it is possible to provide the dropper-type stabilized power circuit which can prevent the reverse current which flows from the output side to the input side. 
     Next, FIG. 2 shows a concrete example of a structure of the compensating resistance switch SW 1 , the output voltage detecting circuit  15 , and the switch driving circuit  16 . In a series regulator  1   a  of FIG. 2, the compensating resistance switch SW 1  is realized with a transistor  21 , and the output voltage detecting circuit  15  is realized with voltage dividing resistances R 3  and R 4 , and the switch driving circuit  16  is realized with a transistor  22 , a resistance R b 1   , a comparator  23 , and a reference voltage circuit  24 . 
     The transistor  21  is a PNP-type transistor. An emitter of the transistor  21  is connected to the emitter (input terminal IN) of the power transistor  11 , and a collector is connected to an end of the high-temperature-leak compensating resistance R EB  which is opposite to a connecting point of the base of the power transistor  11 . Further, a base of the transistor  21  is connected to a collector of a transistor  22 . The transistor  22  is an NPN-type transistor. The collector of the transistor  22  is connected to the base of the transistor  21  as described above, and an emitter is connected to a GND. Further, the base of the transistor  22  is connected to an end of the resistance R b 1   . Another end of the resistance R b 1   is connected to an output terminal of the comparator  23 . 
     The voltage dividing resistances R 3  and R 4  are connected in series between the output terminal OUT and the GND. Further, a junction of the voltage dividing resistance R 3  and the voltage dividing resistance R 4  is connected to an inverting input terminal of the comparator  23 . 
     The reference voltage circuit  24  generates a reference voltage Vref 2  corresponding to the predetermined value of the output voltage detecting circuit  15  described above. Further, an output terminal of the reference voltage circuit  24  is connected to a non-inverting input terminal of the comparator  23 . 
     The comparator  23  compares a divided voltage of the output voltage Vo detected by the voltage dividing resistances R 3  and R 4  with the reference voltage Vref 2 , and judges whether the output voltage is higher or smaller than the predetermined value, and outputs a signal according to the higher/smaller judgement. Power supply lines to the comparator  23  and the reference voltage circuit  24  are supplied from an input line (input terminal IN) of the power transistor  11 . 
     In the foregoing structure, since the divided voltage of the output voltage Vo detected by the voltage dividing resistances R 3  and R 4  is lower than the reference voltage Vref 2  under normal operating conditions, the comparator  23  judges that the output voltage Vo is lower than the predetermined value, and outputs a signal of “High” level. 
     By this, the transistor  22  becomes ON, and a base potential of the transistor  21  becomes “Low” level, and the transistor  21  becomes ON. That is, the switch driving circuit  16  outputs a controlling signal of “Low” level to the compensating resistance switch SW 1 . As a result, the compensating resistance switch SW 1  is conducted, so that the high-temperature-leak compensating resistance R EB  becomes ready to function. On the other hand, when the divided voltage of the output voltage Vo is not less than the reference voltage Vref 2 , the comparator  23  judges that the output voltage Vo is not less than the predetermined value, and outputs a signal of “Low” level. In this way, the transistor  22  becomes OFF, the base potential of the transistor  21  is made “High” level. Thus, the transistor  21  becomes OFF. 
     That is, the switch driving circuit  16  outputs a controlling signal of “High” level to the compensating resistance switch SW 1 . As a result, since the compensating resistance switch SW 1  is not conducted, the high-temperature-leak compensating resistance R EB  is separated from the emitter/base line of the power transistor  11 . Thus, it is possible to prevent the reverse current which flows from the output side to the input side of the series regulator la. 
     Further, the compensating resistance switch SW 1  may be connected like the transistor  21  shown in FIG.  3 . In a series regulator  1   b  of FIG. 3, the emitter of the transistor  21  is connected to the base of the power transistor  11 , and the collector of the transistor  21  is connected to the collector of the transistor  12 . The base of the transistor  21  is connected to the collector of the transistor  22  as in FIG.  2 . The high-temperature-leak compensating resistance R EB  is connected between the emitter of the power transistor  11  and the collector of the transistor  21 . Also in this case, the compensating resistance switch SW 1  is provided in series with the high-temperature-leak compensating resistance R EB  between the emitter and the base of the power transistor  11 , so that it is possible to prevent the reverse current which flows from the output side to the input side of the series regulator  1   b.    
     [Second Embodiment] 
     The following description is to describe another embodiment which realizes a stabilized power circuit of the present invention in reference with FIG. 4 to FIG.  6 . Note that, components having the same functions as the components described in the first embodiment are given the same reference numerals, and descriptions thereof are omitted. 
     FIG. 4 shows a structure of a series regulator  2  as a stabilized power circuit according to the present embodiment. The series regulator  2  includes the power transistor  11 , the driving transistor  12 , the error amplifier  13 , the reference voltage circuit  14 , an output voltage detecting circuit  15 , a switch driving circuit  31 , a reference voltage circuit  32 , voltage dividing resistances R 1  and R 2 , a high-temperature-leak compensating resistance R EB , and a compensating resistance switch SW 1 . 
     The reference voltage circuit  32  supplies a voltage corresponding to the input voltage Vin from the input terminal IN of the series regulator  2  to the switch driving circuit  31 . 
     The switch driving circuit  31  determines the input voltage Vin as the predetermined value described in the first embodiment in accordance with a voltage inputted from the reference voltage circuit  32 , and compares the input voltage Vin with the output voltage Vo detected by the output voltage detecting circuit  15 . According to whether the input voltage Vin is higher or lower than the output voltage Vo, the switch driving circuit  31  outputs a controlling signal which opens or closes the compensating resistance switch SW 1 . The controlling signal is outputted in the same way as in the first embodiment. That is, the output voltage detecting circuit  15 , the switch driving circuit  31 , and the reference voltage circuit  32  make up compensating resistance switch controlling means by which a voltage of the output terminal OUT of the series regulator  2  is detected, and the compensating resistance switch SW 1  is conducted under normal operating conditions, and when the voltage becomes not less than the predetermined value which is equal to the input voltage Vin, the compensating resistance switch SW 1  is not conducted. 
     As a result, even when the voltage of the output side is higher than the input side with the high-temperature-leak compensating resistance provided, it is possible to provide the dropper-type stabilized power circuit which can prevent the reverse current which flows from the output side to the input side. Further, only when voltage of the output terminal is higher than the input voltage, the compensating resistance switch controlling means does not conduct the compensating resistance switch. Thus, it is easy to judges whether or not the voltage of the output terminal is under abnormal conditions in which the reverse current flows from the output side to the input side. 
     Next, FIG. 5 shows a concrete example of a structure of the compensating resistance switch SW 1 , the output voltage detecting circuit  15 , the switch driving circuit  31 , and the reference voltage circuit  32 . In the series regulator  2   a  of FIG. 5, the compensating resistance switch SW 1  is realized with the transistor  21 , and the output voltage detecting circuit  15  is realized with voltage dividing resistances R 5  and R 6 , and the switch driving circuit  31  is realized with the transistor  22 , and the resistance R b 1   , and the comparator  23 , and the reference voltage circuit  32  is realized with the voltage dividing resistances R 5  and R 6  as in the output voltage detecting circuit  15 . The transistors  21  and  22 , the resistance R b 1   , and the comparator  23  are the same components as in FIG.  2 . 
     The voltage dividing resistances R 5  and R 6  of the output voltage detecting circuit  15  are provided in series between the output terminal OUT and the GND, and a junction of the voltage dividing resistance R 5  and the voltage dividing resistance R 6  is connected to the inverting input terminal of the comparator  23 . 
     The voltage dividing resistances R 5  and R 6  of the reference voltage circuit  32  are provided in series between the input terminal IN and the GND, and a junction of the voltage dividing resistance R 5  and the voltage dividing resistance R 6  is connected to the not-inverting input terminal of the comparator  23 . Thus, in the input voltage to the comparator  23 , a voltage ratio of the input voltage Vin and a voltage ratio of the output voltage Vo are equal. 
     A divided voltage of the input voltage Vin of the reference voltage circuit  32  varies due to changes of the input voltage Vin. However, the output voltage Vo of the voltage detecting circuit  15  which is detected as Vref 3  at a certain time is compared with the input voltage Vin, so that whether the input voltage is higher/lower than the output voltage Vo is judged at respective times. 
     In the foregoing structure, the divided voltage of the output voltage Vo of the output voltage detecting circuit  15  is lower than the reference voltage Vref 3  under normal operating conditions. This causes the comparator  23  to judge that the output voltage Vo is lower than the predetermined value (input voltage Vin) and to output a “High” level signal. Thus, the transistor  21  becomes ON state as in the first embodiment. That is, the switch driving circuit  31  outputs a “Low” level controlling signal to the compensating resistance switch SW 1 . As a result, the compensating resistance switch SW 1  is conducted and the high-temperature-leak compensating resistance R EB  becomes ready to function. 
     On the other hand, when the divided voltage of the output voltage Vo is higher than the reference voltage Vref  3 , the comparator  23  judges that the output voltage Vo is higher than the predetermined value (input voltage Vin), and outputs the “Low” level signal. This causes the transistor  21  to be OFF as in the first embodiment. That is, the switch driving circuit  31  outputs a “High” level controlling signal to the compensating resistance switch SW 1 . As a result, the compensating resistance switch SW 1  is not conducted and the high-temperature-leak compensating resistance R EB  is separated from the emitter/base line of the power transistor  11 . Thus, it is possible to prevent the reverse current which flows from the output side to the input side of the series regulator  2   a.    
     Also, the compensating resistance switch SW 1  may be provided as in the transistor  21  shown in FIG.  6 . In a series regulator  2   b  of FIG. 6, the transistor  21  and the high-temperature-leak compensating resistance R EB  are provided in the same positioning relation as in the series regulator  1   b  of FIG.  3 . In this case, the compensating resistance switch SW 1  is provided between the emitter and the base of the power transistor  11  in straight with the high-temperature-leak compensating resistance R EB , so that it is possible to prevent the reverse current which flows from the output side to the input side of the series regulator  2   b.    
     [Third Embodiment] 
     The following description is to describe still another embodiment which realizes the stabilized power circuit of the present invention in reference with FIG. 7 to FIG.  10 . Note that, components having the same functions as the components described in the first and second embodiments are given the same reference numerals, and descriptions thereof are omitted. 
     FIG. 7 shows a structure of a series regulator  3  as the stabilized power circuit according to the present embodiment. The series regulator  3  includes the power transistor  11 , the driving transistor  12 , the error amplifier  13 , the reference voltage circuit  14 , the output voltage detecting circuit  15 , the switch driving circuit  16 , the voltage dividing resistances R 1  and R 2 , the high-temperature-leak compensating resistance R EB , the compensating resistance switch SW 1 , and a power switch SW 2 . 
     The power switch SW 2  is inserted in any point of a power supply line supplied from the input side of the power transistor  11  to the error amplifier  13  and the reference voltage circuit  14 . Further, this power switch SW 2  is conducted or not conducted, based on the output voltage Vo detected by the output voltage detecting circuit  15 , by the same controlling signal as the controlling signal which is outputted from the switch driving circuit  16  to the compensating resistance switch SW 1 . 
     That is, under normal operating conditions, the power switch SW 2  is conducted so that power is supplied to circuits such as the error amplifier  13  and the reference voltage circuit  14  which perform a voltage stabilizing operation, and when the voltage of the output terminal OUT becomes not less than the predetermined value described in the first and second embodiments, the power switch SW 2  is not conducted so that power is not supplied to the circuits which perform a voltage stabilizing operation. When the power switch SW 2  is not conducted, the error amplifier  13  and the reference voltage circuit  14  stop the voltage stabilizing operation. 
     Thus, the output voltage detecting circuit  15 , the switch driving circuit  16 , and the power switch SW 2  make up operation stopping means by which when voltage of the output terminal OUT becomes not less than the predetermined value, the voltage stabilizing operation is stopped. By this, when the voltage of the output terminal OUT becomes not less than the predetermined value, an operating current of the circuit which performs a voltage stabilizing operation is reduced. Further, since the voltage of the output terminal OUT is not less than the predetermined value under abnormal operating conditions, the error amplifier  13  and the reference voltage circuit  14  stop the voltage stabilizing operation, so that it is possible to reduce power consumption of the stabilized power circuit without any problem. 
     Further, the output voltage detecting circuit  15  and the switch driving circuit  16  make up power switch controlling means by which conduction or non-conduction of the power switch SW 2  is controlled, and the operation stopping means stops supplying power to the circuit which performs the voltage stabilizing operation and stops the voltage stabilizing operation by including the output voltage detecting circuit  15 , the switch driving circuit  16 , and the power switch SW 2  as described above. Thus, it is possible to restrict the current in the foregoing circuit to a low value such as not more than microampere when the voltage stabilizing operation is stopped. As a result, it is possible to reduce power consumption of the stabilized power circuit greatly. 
     Further, in the compensating resistance switch controlling means which is made up of the power switch controlling means, the output voltage detecting circuit  15  described in the first and second embodiments, and the switch driving circuit  16 , the components may be independent from each other. However, it is preferable that the compensating resistance switch controlling means serves as the power switch controlling means as shown in FIG.  7 . 
     In this case, the compensating resistance switch controlling means which controls conduction or non-conduction of the compensating resistance switch SW 1  also controls conduction or non-conduction of the power switch SW 2 . However, as long as the compensating resistance switch SW 1  and the power switch SW 2  are switched from conduction to non-conduction in synchronism with each other, it is possible to control conduction or non-conduction of them by using the compensating resistance switch controlling means, that is, by using the same output of the power switch controlling means. 
     Further, a circuit which detects the voltage of the output terminal OUT can also be controlled by the both switch as in the output voltage detecting circuit  15 . Thus, it is possible to simplify a structure of the circuit, and it is not required to take variety of voltage detection of the output terminal OUT into consideration. 
     Note that, in the output voltage detecting circuit  15  and the switch driving circuit  16  which make up the compensating resistance switch controlling means and the power switch controlling means respectively, for example, the single output voltage detecting circuit  15  may be provided with two switch driving circuits  16  which correspond to the switch for compensating resistance  1  and the power switch  2  provided. 
     That is, one of the output voltage detecting circuit  15  and the power switch driving circuit  16  is solely provided and the other is pluralized so as to be provided in plural. Thus, it is possible to simplify the structure of the circuit. 
     Next, FIG. 8 shows a concrete example of a structure of the power switch SW 2 , the output voltage detecting circuit  15 , and the switch driving circuit  16 . In a series regulator  3   a  of the FIG. 8, the power switch SW 2  is realized with a transistor  41 , and the output voltage detecting circuit  15  is realized with the voltage dividing resistances R 3  and R 4 , and the switch driving circuit  16  is realized with a transistor  42 , the resistance R b 2   , the comparator  23 , and the reference voltage circuit  24 . The voltage dividing resistances R 3  and R 4 , the comparator  23 , and the reference voltage circuit  24  are the same components as in FIG.  2 . Further, it is possible to realize the compensating resistance switch SW 1  and a circuit supplied from the comparator  23  to the compensating resistance switch SW 1  by using the same components of FIG.  2 . In these components, the transistor  42  can serve as the transistor  22 , and also the resistance R b 2   can serve as the resistance R b 1   . FIG. 8 is a diagram which shows at least the power switch controlling means. 
     The transistor  41  is a PNP-type transistor, and an emitter of the transistor  41  is connected to an input line (input terminal IN) of the power transistor  11 , and a collector of the transistor  41  is connected to respective power terminals of the error amplifier  13  and the reference voltage circuit  14 . Further, a base of the transistor  41  is connected to the collector of the transistor  42 . 
     The transistor  42  is an NPN-type transistor, and the collector is connected to the base of the transistor  41  and the emitter is connected to the GND as described above. Further, the base of the transistor  42  is connected to an end of the resistance R b 2   . Another end of the resistance R b 2   is connected to the output terminal of the comparator  23 . 
     In the foregoing structure, since the divided voltage of the output voltage Vo detected by the voltage dividing resistances R 3  and R 4  is lower than the reference voltage Vref 2  under normal operating conditions, the comparator  23  judges that the output voltage Vo is lower than the predetermined value, and outputs a “High” level signal. By this, the transistor  42  becomes ON, and makes base potential of the transistor  41  a “Low” level. That is, the switch driving circuit  16  outputs a “Low” level controlling signal to the power switch SW 2 . As a result, the power switch SW 2  is conducted, and power supply to the error amplifier  13  and the reference voltage circuit  14  which has been performed since the rise continues. 
     Further, at the same time, the compensating resistance switch SW 1  is conducted, so that the high-temperature-leak compensating resistance R EB  becomes ready to function. While, when the divided voltage of the output voltage is higher than the reference voltage Vref 2 , the comparator  23  judges that the output voltage Vo is higher than the predetermined value, and outputs a “Low” level signal. This makes the transistor  42  OFF, and the base potential of the transistor  41  becomes “High” level. Then, the transistor  41  becomes OFF. That is, the switch driving circuit  16  outputs a “High” level controlling signal to the power switch SW 2 . As a result, the power switch SW 2  is not conducted, and stop supplying power to the error amplifier  13  and the reference voltage circuit  14 . Further, at the same time, the compensating resistance switch SW 1  is not conducted, so that the high-temperature-leak compensating resistance R EB  is separated from the emitter/base line of the power transistor  11 . Thus, it is possible to prevent the reverse current which flows from the output side to the input side of the series regulator  3   a , and it is possible to reduce the operating current of the error amplifier  13  and the reference voltage circuit  14 . 
     FIG. 9 shows another concrete example of the structure of the power switch SW 2 , the output voltage detecting circuit  15 , and the switch driving circuit  16 . In a series regulator  3   b  of FIG. 9, the power switch SW 2  is realized with the transistor  41 , and the output voltage detecting circuit  15  is realized with voltage dividing resistances R 30  and R 40 , and the switch driving circuit  16  is realized with the transistors  42 ,  43 , and a resistance R b 3   . The transistors  41  and  42  are the same components as in FIG.  8 . Further, the compensating resistance switch SW 1  and the compensating resistance switch controlling means can be realized with the same components as in FIG.  2 . Further, it is possible that the transistor  21  of FIG. 2 is used as the compensating resistance switch SW 1 , and a base of the transistor  21  is connected to a base of the transistor  41  of FIG. 9, and the transistor  42  and the resistance R b 3   are used as the switch for compensating resistance controlling means and the power switch controlling means. FIG. 8 shows at least the compensating resistance switch controlling means. 
     The voltage dividing resistances R 30  and R 40  are provided in series between the output terminal OUT and the GND. The transistor  43  is an NPN-type transistor, and the base is connected to a junction of the voltage dividing resistances R 30  and R 40 , and the collector is connected to the base of the transistor  42 , and the emitter is connected to the GND. 
     The resistance Rb 3  is provided between the emitter of the transistor  41  and the base of the transistor  42 . 
     Respective resistance values of the voltage dividing resistances R 30  and R 40  is set so that when the output voltage Vo is equal to the predetermined value, the divided voltage is equal to a threshold value voltage of the base/emitter line of the transistor  43 . 
     In the foregoing structure, the divided voltage of the output voltage detected by the voltage dividing resistances R 30  and R 40  is lower than the threshold value of the base/emitter line of the transistor  43 , so that the transistor  43  becomes OFF. Then, the base potential of the transistor  42  becomes “High” level. This causes the transistor  42  to be ON, so that the base potential of the transistor  41  becomes “Low” level. As a result, the transistor  41  becomes ON. That is, the switch driving circuit  16  outputs a “Low” level controlling signal to the power switch SW 2 , so that the power switch SW 2  is conducted. Thus, supplying power to the error amplifier  13  and the reference voltage circuit  14  which has been performed since the rise continues. 
     Further, at the same time, the compensating resistance switch SW 1  is conducted, so that the high-temperature-leak compensating resistance R EB  becomes ready to function. While, when the output voltage Vo becomes not less than the predetermined value, the divided voltage of the output voltage Vo detected by the voltage dividing resistances R 30  and R 40  becomes not less than the threshold value of the base/emitter of the transistor  43 . As a result, the transistor  43  becomes ON, and the base potential of the transistor  42  becomes low level. 
     This makes the transistor  42  OFF, so that the base potential of the transistor  41  becomes “High” level. As a result, the transistor  41  becomes OFF. That is, the switch driving circuit  16  outputs a “High” level controlling signal to the power switch SW 2 , and the power switch SW 2  is not conducted and stops supplying power to the error amplifier  13  and the reference voltage circuit  14 . 
     Further, at the same time, the compensating resistance switch SW 1  is not conducted, so that the high-temperature-leak compensating resistance R EB  is separated from the emitter/base line of the power transistor  11 . Thus, it is possible to prevent the reverse current which flows from the output side to the input side of the series regulator  3   b . Moreover, it is possible to reduce the operating current of the error amplifier  13  and the reference voltage circuit  14 . 
     Further, in the present embodiment, the switch driving circuit  16  of FIG. 7 may be replaced with the switch driving circuit  31  and the reference voltage circuit  32  of FIG.  4 . In this case, the output voltage detecting circuit  15 , the switch driving circuit  31 , and the reference voltage circuit  32  make up the compensating resistance switch controlling means, and also make up the power switch controlling means. 
     FIG. 10 shows a concrete example of a structure of the power switch SW 2 , the output voltage detecting circuit  15 , a switch driving circuit  31 , and a reference voltage circuit  32 . In a series regulator  3   c  of FIG. 10, the power switch SW 2  is realized with a transistor  41 , and the output voltage detecting circuit  15  is realized with the voltage dividing resistances R 5  and R 6 , and the switch driving circuit  31  is realized with the transistor  42 , the resistance R b 2   , and the comparator  23 , and the reference voltage circuit  32  is realized with the voltage dividing resistances R 5  and R 6  as in the output voltage detecting circuit  15 . The transistors  41  and  42 , the resistance R b 2   , and the comparator  23  are the same components as in FIG. 8, and the voltage dividing resistances R 5  and R 6  are the same components as in FIG.  5 . Further, the compensating resistance switch SW 1  and a circuit supplied from the comparator  23  to the compensating resistance switch SW 1  are the same positioning relation as in FIG.  8 . 
     In the structure, the divided voltage of the output voltage Vo of the output voltage detecting circuit  15  is lower than the reference voltage Vref 3 , so that the comparator  23  judges that the output voltage Vo is lower than the predetermined value (input voltage Vin) and outputs a “High” level signal. This makes the transistor  41  become ON as in FIG.  8 . While, when the divided voltage of the output voltage Vo is higher than the reference voltage Vref 3 , the comparator  23  judges that the output voltage Vo is higher than the predetermined value (input voltage Vin) and outputs a “Low” level signal. This makes the transistor  41  become OFF as in FIG.  8 . 
     [Fourth Embodiment] 
     The following description is to describe still another embodiment which realizes a stabilized power circuit of the present invention in reference with FIG.  11  and FIG.  12 . Note that, components having the same functions as the components described in the first to third embodiments are given the same reference numerals, and descriptions thereof are omitted. 
     FIG. 11 shows a structure of a series regulator  4   a  as a stabilized power circuit according to the present embodiment. The series regulator  4   a  is deferent from the series regulator  3   b  of FIG. 9 in that the voltage dividing resistances R 1  and R 2  are replaced with the voltage dividing resistances R 10 , R 11 , and R 2 , and the voltage dividing resistances R 10 , R 11 , and R 2  function as the voltage dividing resistances R 30  and R 40 . 
     The voltage dividing resistances R 10 , R 11 , and R 2  are provided in series between the output terminal OUT and the GND. A junction of the voltage dividing resistance R 11  and the voltage dividing resistance R 2  is connected to the inverting input terminal of the error amplifier  13 . A junction of the voltage dividing resistance R 10  and the voltage dividing resistance R 11  is connected to the base of the transistor  43 . Resistance values of the voltage dividing resistances R 1 , R 2 , R 10 , R 11 , R 30 , and R 40  are r 1 , r 2 , r 10 , r 11 , r 30 , and r 40  respectively. Between these resistance values, there exists the following relation. r 1 =r 10 +r 11 , r 10 /(r 10 +r 11 +r 2 )=r 30 /(r 30 +r 40 ). 
     That is, in the series regulator  4   a , the voltage dividing resistances R 10 , R 11 , and R 2  for output voltage feedback serve as the output voltage detecting circuit  15  of FIG. 7, and the compensating resistance switch controlling means and the power switch controlling means detect the voltage of the output terminal OUT by using the voltage dividing resistances R 10 , R 11 , and R 2 . Thus, it is possible to reduce the number of elements provided as voltage dividing circuits between the output terminal OUT and the GND, for example, it is possible to reduce the number from two in FIG. 9 to one in FIG.  11 . 
     Further, FIG. 12 shows a structure of a series regulator  4   b  as a stabilized power circuit according to the present embodiment. The series regulator  4   b  is deferent from the series regulator  3   c  of FIG. 10 in that two pairs of the voltage dividing resistances R 5  and R 6  are replaced with the voltage dividing resistances R 1 , R 20 , and R 21  respectively, and the voltage dividing resistances R 1 , R 20 , and R 21  have a function of a voltage dividing resistance as the output voltage detecting circuit  15  (FIG. 4) and a function of a voltage dividing resistance for output voltage feedback used for the voltage stabilizing operation. 
     The circuit for output voltage feedback and the voltage dividing resistances R 1 , R 20 , and R 21  as the output voltage detecting circuit  15  are provided in series between the output terminal OUT and the GND. A junction of the voltage dividing resistance R 20  and the voltage dividing resistance R 21  is connected to the inverting input terminal of the error amplifier  13 . A junction of the voltage dividing resistance R 20  and the voltage dividing resistance R 21  is connected to the inverting input terminal of the comparator  23 . The voltage dividing resistances R 1 , R 20 , and R 21  as the reference voltage circuit  32  (FIG. 4) is provided in series between the input terminal IN and the GND. A junction of the voltage dividing resistance R 1  and the voltage dividing resistance R 20  is connected to the non-inverting input terminal of the comparator  23 . Resistance values of the voltage dividing resistances R 1 , R 2 , R 5 , R 6 , R 20 , and R 21  are r 1 , r 2 , r 5 , r 6 , r 20 , and r 21  respectively. Between these resistance values, there exists the following relation. r 2 =r 20 +r 21 , (r 1 +r 20 )/(r 1 +r 20 +r 21 )=r 5 /(r 5 +r 6 ). 
     Also in this case, it is possible to reduce the number of elements provided as voltage dividing circuits between the output terminal OUT and the GND as in FIG.  11 . 
     Note that, like the example described above, it is possible to apply the structure in which the voltage dividing resistance for the output voltage feedback serves as the output voltage detecting circuit  15  to all the series regulators described above. 
     [Fifth Embodiment] 
     The following description is to describe still another embodiment which realizes a stabilized power circuit of the present invention in reference with FIG.  13 . Note that, components having the same functions as the components described in the first to fourth embodiments are given the same reference numerals, and descriptions thereof are omitted. 
     FIG. 13 shows a structure of a series regulator  5   a  as a stabilized power circuit according to the present embodiment. The series regulator  5   a  is different from the series regulator  4   a  of FIG. 11 in that the high-temperature-leak compensating resistance R EB  is provided between the base of the transistor  11  and the collector of the transistor  41 , and the compensating resistance switch SW 1  is removed. 
     In this case, the transistor  41  of FIG. 13 functions as a switch which serves as the compensating resistance switch SW 1  and the power switch SW 2 . That is, a power supply line to the circuit which performs a power stabilizing operation is taken from the input side of the power transistor  11  through the path to the high-temperature-leak compensating resistance R EB , and the switch serves as the compensating resistance switch SW 1  and the power switch SW 2  is provided in the path. 
     As long as the compensating resistance switch SW 1  and the power switch SW 2  are switched for conduction/non-conduction in synchronism with each other, it is possible to realize this structure. This enables the circuit structure to be simplified. Moreover, it is not required to consider a timing gap of operation which occurs between the compensating resistance switch SW 1  and the power switch SW 2 . 
     Generally, the switch which serves as the compensating resistance switch SW 1  and the power switch SW 2  supplies the power supply line to circuits such as the error amplifier  13  and the reference voltage circuit  14  which perform power stabilizing operation from the input side of the power transistor  11 . Further, in the structure in which the high-temperature-leak compensating resistance R EB  is provided between any point of the power supply line and the base of the power transistor  11 , the switch which serves as the compensating resistance switch SW 1  and the power switch SW 2  is provided between (1) a junction of the power supply line and the high-temperature-leak compensating resistance R EB  and ( 2 ) a junction of the power supply line and the input line. 
     [Sixth Embodiment] 
     The following description is to describe still another embodiment which realizes a stabilized power circuit of the present invention in reference with FIG.  14 . Note that, components having the same functions as the components described in the first to fifth embodiments are given the same reference numerals, and descriptions thereof are omitted. 
     FIG. 14 shows a structure of a series regulator  6   a  as a stabilized power circuit according to the present embodiment. The series regulator  6   a  is different from the series regulator  5   a  of FIG. 13 in that the resistance R b 3   is removed, and the emitter of the transistor  41  is separated from the base of the transistor  42 , and a terminal CTRL is connected via the resistance R b 4   to the base of the transistor  42 . The terminal CTRL is a terminal which externally receives an operation signal Vc which operates the operation stopping means including the transistors  42  and  43 , and the voltage dividing resistances R 10 , R 11 , and R 2 . 
     Under normal operating conditions, the base potential of the transistor  43  is “Low” and becomes OFF, and a “High” level voltage as an operation signal Vc is given to the terminal CTRL. As a result, the transistor  42  and the transistor  41  become ON. 
     When the “High” level voltage is applied to the terminal CTRL, a resistance value of the resistance R b 4   is set so that a voltage of the base/emitter of the transistor  42  is higher than threshold value. When the output voltage is higher than the predetermined value, the transistor  43  becomes ON, so that the base potential of the transistor  42  becomes “Low” level. As a result, the transistor  42  becomes OFF and the transistor  41  becomes OFF. However, the “Low” level voltage as the operation signal Vc is given to the terminal CTRL also under normal operating conditions, so that the transistor  42  becomes OFF and the transistor  41  becomes OFF. 
     In this way, by providing the terminal CTRL, it is possible to input an appropriate operation signal Vc from the terminal CTRL in a case where the voltage stabilizing operation is to be stopped from outside, including a case where the voltage of the output terminal OUT is abnormal. 
     Thus, it is not required to additionally provide a circuit for ON/OFF of a normal power supply, so that the circuit can be simplified. However, when the voltage of the output terminal OUT is not less than the predetermined value, it is preferable that the structure is arranged so that the voltage stabilizing operation cannot be performed as in the structure of FIG. 14, even when the operation signal Vc is inputted from the terminal CTRL. 
     Further, the stabilized power circuit of the present invention which is a dropper-type stabilized power circuit including a PNP-type transistor and a high-temperature-leak compensating resistance provided between an emitter and a base of the power transistor, includes a compensating resistance switch provided in series with the high-temperature-leak compensating resistance between the emitter and the base; and compensating resistance switch controlling means which detects a voltage of the output terminal, and conducts the compensating resistance switch under normal operating conditions in which the output voltage is obtained by dropping an input voltage, and does not conduct the compensating resistance switch when the foregoing voltage is higher than the output voltage under normal operating conditions and higher than a predetermined value which was set to be lower than a value at which a current begins to flow from a collector to the base of the power transistor. 
     Further, the stabilized power circuit of the present invention can be arranged so that the foregoing predetermined value is equal to the input voltage. 
     According to the invention, only when the voltage of the output terminal becomes not less than the input voltage, the compensating resistance switch controlling means does not conduct the compensating resistance switch. Thus, it is possible to easily judges that the voltage of the output terminal is under abnormal conditions in which the reverse current flows from the output side to the input side. 
     Further, the stabilized power circuit of the present invention may be arranged so that the compensating resistance switch controlling means detects the voltage of the output terminal by using the voltage dividing resistance for the output voltage feedback used to perform the voltage stabilizing operation. 
     According to the present invention, the voltage dividing resistance is used to detects the voltage of the output terminal brought about by the compensating resistance switch controlling means. Thus, it is possible to reduce the number of the elements. 
     Further, the stabilized power circuit of the present invention can be arranged so as to further include operation stopping means which stops the voltage stabilizing operation when the voltage of the output terminal becomes not less than the predetermined value. 
     According to the foregoing invention, when a voltage of the output terminal becomes not less than the predetermined value, a reverse current is prevented from flowing from the output side to the input side. Since the operation stopping means stops the voltage stabilizing operation, the operating current of a circuit which performs the voltage stabilizing operation is reduced. Further, since it is under abnormal conditions that a voltage of the output terminal is not less than the predetermined value, it is possible to reduce consumption power of the stabilized power circuit without any problem by stopping the voltage stabilizing operation. 
     Further, the stabilized power circuit of the present invention can be arranged so as to include a power switch which conducts the operation stopping means so as to supply power to a circuit which performs the voltage stabilizing operation under normal operating conditions, and does not conduct itself when a voltage of the output terminal becomes not less than the predetermined value so as to stop supplying power to the circuit which performs the stabilizing voltage operation, and the power switch controlling means which detects a voltage of the output terminal so as to control conduction or non-conduction of the power switch. 
     According to the foregoing invention, the power switch and the power switch controlling means are used as the operation stopping means to stop supplying power to circuits such as an error amplifier and its reference voltage circuit which perform the voltage stabilizing operation, so that the voltage stabilizing operation is stopped. Thus, it is possible to restrict current in the circuit to a low value such as not more than microampere when the voltage stabilizing operation is stopped, so that it is possible to reduce consumption power of the stabilized power circuit greatly. 
     Further, the stabilized power circuit of the present invention can be arranged so that the compensating resistance switch controlling means serves as the power switch controlling means. 
     According to the foregoing invention, the compensating resistance switch controlling means which controls conduction or non-conduction of the compensating resistance switch also controls conduction or non-conduction of the power switch. As long as the compensating resistance switch and the power switch are switched for conduction/non-conduction in synchronism with each other, it is possible to control by using the same output of the compensating resistance switch controlling means, that is, the same output as the power switch controlling means. Further, it is possible to use a voltage detecting circuit of the output terminal as the both switches at. Thus, the structure of the circuit can be simplified, and it is not required to take variety of voltage detection of the output terminal voltage into consideration. 
     Further, the stabilized power circuit of the present invention can be arranged so that a power supply line to the circuit which performs the voltage stabilizing operation is taken from the input line of the power transistor, and the high-temperature-leak compensating resistance is provided between any point of the power supply line and the base of the power transistor, and a switch which serves as the compensating resistance switch and the power switch is provided between (1) a junction of the power supply line and the high-temperature-leak compensating resistance and (2) a junction of the power supply line and the input line. 
     According to the foregoing invention, the power supply line to the circuit which performs the voltage stabilizing operation is taken from the input side of the power transistor and provided in the same path as a path to the high-temperature-leak compensating resistance, and the switch which serves as the compensating resistance switch and the power switch is provided in the path. Thus, the structure of the circuit can be simplified, and it is not required to consider the timing gap which occurs between the both switches. 
     Further, the stabilized power circuit can be arranged so as to further include a terminal which receives, from outside, an operation signal which operates the operation stopping means. 
     According to the foregoing invention, in a case where the voltage stabilizing operation is to be stopped from outside, including a case where the voltage of the output terminal is abnormal, it is possible to operates the operation stopping means by inputting the operating signal from the terminal. Thus, it is not required to provide an ON/OFF circuit of a normal power supply, so that the circuit can be simplified. 
     The invention being thus described, it will be obvious that the same may be varied in many ways. Such variations are not to be regarded as a departure from the spirit and scope of the invention, and all such modifications as would be obvious to one skilled in the art are intended to be included within the scope of the following claims.