Patent Publication Number: US-2022231723-A1

Title: Advanced backhaul services

Description:
CROSS-REFERENCE TO RELATED APPLICATIONS 
     This application is a continuation of U.S. patent application Ser. No. 16/900,524, filed Jun. 12, 2020, currently pending, which is a continuation of U.S. patent application Ser. No. 16/282,192, filed Feb. 21, 2020, now U.S. Pat. No. 10,700,733, which is a continuation of U.S. patent application Ser. No. 15/873,251, filed Jan. 17, 2018, now U.S. Pat. No. 10,284,253, which is a continuation of U.S. patent application Ser. No. 14/666,294, filed Mar. 23, 2015, now U.S. Pat. No. 9,876,530, which is a continuation of U.S. patent application Ser. No. 14/098,456, filed on Dec. 5, 2013, now U.S. Pat. No. 8,989,762, the disclosure of which are incorporated herein by reference in their entirety. 
    
    
     BACKGROUND 
     1. Field 
     The present disclosure relates generally to data networking and in particular to a backhaul radio for connecting remote edge access networks to core networks. 
     2. Related Art 
     Data networking traffic has grown at approximately 100% per year for over 20 years and continues to grow at this pace. Only transport over optical fiber has shown the ability to keep pace with this ever-increasing data networking demand for core data networks. While deployment of optical fiber to an edge of the core data network would be advantageous from a network performance perspective, it is often impractical to connect all high bandwidth data networking points with optical fiber at all times. Instead, connections to remote edge access networks from core networks are often achieved with wireless radio, wireless infrared, and/or copper wireline technologies. 
     Radio, especially in the form of cellular or wireless local area network (WLAN) technologies, is particularly advantageous for supporting mobility of data networking devices. However, cellular base stations or WLAN access points inevitably become very high data bandwidth demand points that require continuous connectivity to an optical fiber core network. 
     When data aggregation points, such as cellular base station sites, WLAN access points, or other local area network (LAN) gateways, cannot be directly connected to a core optical fiber network, then an alternative connection, using, for example, wireless radio or copper wireline technologies, must be used. Such connections are commonly referred to as “backhaul.” 
     Many cellular base stations deployed to date have used copper wireline backhaul technologies such as T1, E1, DSL, etc. when optical fiber is not available at a given site. However, the recent generations of HSPA+ and LTE cellular base stations have backhaul requirements of 100 Mb/s or more, especially when multiple sectors and/or multiple mobile network operators per cell site are considered. WLAN access points commonly have similar data backhaul requirements. These backhaul requirements cannot be practically satisfied at ranges of 300 m or more by existing copper wireline technologies. Even if LAN technologies such as Ethernet over multiple dedicated twisted pair wiring or hybrid fiber/coax technologies such as cable modems are considered, it is impractical to backhaul at such data rates at these ranges (or at least without adding intermediate repeater equipment). Moreover, to the extent that such special wiring (i.e., CAT 5/6 or coax) is not presently available at a remote edge access network location; a new high capacity optical fiber is advantageously installed instead of a new copper connection. 
     Rather than incur the large initial expense and time delay associated with bringing optical fiber to every new location, it has been common to backhaul cell sites, WLAN hotspots, or LAN gateways from offices, campuses, etc. using microwave radios. An exemplary backhaul connection using the microwave radios  132  is shown in  FIG. 1 . Traditionally, such microwave radios  132  for backhaul have been mounted on high towers  112  (or high rooftops of multi-story buildings) as shown in  FIG. 1 , such that each microwave radio  132  has an unobstructed line of sight (LOS)  136  to the other. These microwave radios  132  can have data rates of 100 Mb/s or higher at unobstructed LOS ranges of 300 m or longer with latencies of 5 ms or less (to minimize overall network latency). 
     Traditional microwave backhaul radios  132  operate in a Point-to-point (PTP) configuration using a single “high gain” (typically &gt;30 dBi or even &gt;40 dBi) antenna at each end of the link  136 , such as, for example, antennas constructed using a parabolic dish. Such high gain antennas mitigate the effects of unwanted multipath self-interference or unwanted co-channel interference from other radio systems such that high data rates, long range and low latency can be achieved. These high gain antennas however have narrow radiation patterns. 
     Furthermore, high gain antennas in traditional microwave backhaul radios  132  require very precise, and usually manual, physical alignment of their narrow radiation patterns in order to achieve such high performance results. Such alignment is almost impossible to maintain over extended periods of time unless the two radios have a clear unobstructed line of sight (LOS) between them over the entire range of separation. Furthermore, such precise alignment makes it impractical for any one such microwave backhaul radio to communicate effectively with multiple other radios simultaneously (i.e., a “point-to-multipoint” (PMP) configuration). 
     In wireless edge access applications, such as cellular or WLAN, advanced protocols, modulation, encoding and spatial processing across multiple radio antennas have enabled increased data rates and ranges for numerous simultaneous users compared to analogous systems deployed 5 or 10 years ago for obstructed LOS propagation environments where multipath and co-channel interference were present. In such systems, “low gain” (usually &lt;6 dBi) antennas are generally used at one or both ends of the radio link both to advantageously exploit multipath signals in the obstructed LOS environment and allow operation in different physical orientations as would be encountered with mobile devices. Although impressive performance results have been achieved for edge access, such results are generally inadequate for emerging backhaul requirements of data rates of 100 Mb/s or higher, ranges of 300 m or longer in obstructed LOS conditions, and latencies of 5 ms or less. 
     In particular, “street level” deployment of cellular base stations, WLAN access points or LAN gateways (e.g., deployment at street lamps, traffic lights, sides or rooftops of single or low-multiple story buildings) suffers from problems because there are significant obstructions for LOS in urban environments (e.g., tall buildings, or any environments where tall trees or uneven topography are present). 
       FIG. 1  illustrates edge access using conventional unobstructed LOS PTP microwave radios  132 . The scenario depicted in  FIG. 1  is common for many 2 nd  Generation (2G) and 3 rd  Generation (3G) cellular network deployments using “macrocells”. In  FIG. 1 , a Cellular Base Transceiver Station (BTS)  104  is shown housed within a small building  108  adjacent to a large tower  112 . The cellular antennas  116  that communicate with various cellular subscriber devices  120  are mounted on the towers  112 . The PTP microwave radios  132  are mounted on the towers  112  and are connected to the BTSs  104  via an nT1 interface. As shown in  FIG. 1  by line  136 , the radios  132  require unobstructed LOS. 
     The BTS on the right  104   a  has either an nT1 copper interface or an optical fiber interface  124  to connect the BTS  104   a  to the Base Station Controller (BSC)  128 . The BSC  128  either is part of or communicates with the core network of the cellular network operator. The BTS on the left  104   b  is identical to the BTS on the right  104   a  in  FIG. 1  except that the BTS on the left  104   b  has no local wireline nT1 (or optical fiber equivalent) so the nT1 interface is instead connected to a conventional PTP microwave radio  132  with unobstructed LOS to the tower on the right  112   a . The nT1 interfaces for both BTSs  104   a ,  104   b  can then be backhauled to the BSC  128  as shown in  FIG. 1 . 
       FIG. 2A  is a block diagram of the major subsystems of a conventional PTP microwave radio  200 A for the case of Time-Division Duplex (TDD) operation, and  FIG. 2B  is a block diagram of the major subsystems of a conventional PTP microwave radio  200 B for the case of Frequency-Division Duplex (FDD) operation. 
     As shown in  FIG. 2A  and  FIG. 2B , the conventional PTP microwave radio traditionally uses one or more (i.e. up to “n”) T1 interfaces  204 A and  204 B (or in Europe, E1 interfaces). These interfaces ( 204 A and  204 B) are common in remote access systems such as 2G cellular base stations or enterprise voice and/or data switches or edge routers. The T1 interfaces are typically multiplexed and buffered in a bridge (e.g., the Interface Bridge  208 A,  208 B) that interfaces with a Media Access Controller (MAC)  212 A,  212 B. 
     The MAC  212 A,  212 B is generally denoted as such in reference to a sub-layer of Layer 2 within the Open Systems Interconnect (OSI) reference model. Major functions performed by the MAC include the framing, scheduling, prioritizing (or “classifying”), encrypting and error checking of data sent from one such radio at  FIG. 2A  or  FIG. 2B  to another such radio. The data sent from one radio to another is generally in a “user plane” if it originates at the T1 interface(s) or in the “control plane” if it originates internally such as from the Radio Link Controller (RLC)  248 A,  248 B shown in  FIG. 2A  or  FIG. 2B . 
     With reference to  FIGS. 2A and 2B , the Modem  216 A,  216 B typically resides within the “baseband” portion of the Physical (PHY) layer 1 of the OSI reference model. In conventional PTP radios, the baseband PHY, depicted by Modem  216 A,  216 B, typically implements scrambling, forward error correction encoding, and modulation mapping for a single RF carrier in the transmit path. In receive, the modem typically performs the inverse operations of demodulation mapping, decoding and descrambling. The modulation mapping is conventionally Quadrature Amplitude Modulation (QAM) implemented with In-phase (I) and Quadrature-phase (Q) branches. 
     The Radio Frequency (RF)  220 A,  220 B also resides within the PHY layer of the radio. In conventional PTP radios, the RF  220 A,  220 B typically includes a single transmit chain (Tx)  224 A,  224 B that includes I and Q digital to analog converters (DACs), a vector modulator, optional upconverters, a programmable gain amplifier, one or more channel filters, and one or more combinations of a local oscillator (LO) and a frequency synthesizer. Similarly, the RF  220 A,  220 B also typically includes a single receive chain (Rx)  228 A,  228 B that includes I and Q analog to digital converters (ADCs), one or more combinations of an LO and a frequency synthesizer, one or more channel filters, optional downconverters, a vector demodulator and an automatic gain control (AGC) amplifier. Note that in many cases some of the one or more LO and frequency synthesizer combinations can be shared between the Tx and Rx chains. 
     As shown in  FIGS. 2A and 2B , conventional PTP radios  200 A,  200 B also include a single power amplifier (PA)  232 A,  232 B. The PA  232 A,  232 B boosts the transmit signal to a level appropriate for radiation from the antenna in keeping with relevant regulatory restrictions and instantaneous link conditions. Similarly, such conventional PTP radios  232 A,  232 B typically also include a single low-noise amplifier (LNA)  236 ,  336  as shown in  FIGS. 2A and 2B . The LNA  236 A,  236 B boosts the received signal at the antenna while minimizing the effects of noise generated within the entire signal path. 
     As described above,  FIG. 2A  illustrates a conventional PTP radio  200 A for the case of TDD operation. As shown in  FIG. 2A , conventional PTP radios  200 A typically connect the antenna  240 A to the PA  232 A and LNA  236 A via a band-select filter  244 A and a single-pole, single-throw (SPST) switch  242 A. 
     As described above,  FIG. 2B  illustrates a conventional PTP radio  200 B for the case of FDD operation. As shown in  FIG. 2B , in conventional PTP radios  200 B, then antenna  240 B is typically connected to the PA  232 B and LNA  236 B via a duplexer filter  244 B. The duplexer filter  244 B is essentially two band-select filters (tuned respectively to the Tx and Rx bands) connected at a common point. 
     In the conventional PTP radios shown in  FIGS. 2A and 2B , the antenna  240 A,  240 B is typically of very high gain such as can be achieved by a parabolic dish so that gains of typically &gt;30 dBi (or even sometimes &gt;40 dBi), can be realized. Such an antenna usually has a narrow radiation pattern in both the elevation and azimuth directions. The use of such a highly directive antenna in a conventional PTP radio link with unobstructed LOS propagation conditions ensures that the modem  216 A,  216 B has insignificant impairments at the receiver (antenna  240 A,  240 B) due to multipath self-interference and further substantially reduces the likelihood of unwanted co-channel interference due to other nearby radio links. 
     Although not explicitly shown in  FIGS. 2A and 2B , the conventional PTP radio may use a single antenna structure with dual antenna feeds arranged such that the two electromagnetic radiation patterns emanated by such an antenna are nominally orthogonal to each other. An example of this arrangement is a parabolic dish. Such an arrangement is usually called dual-polarized and can be achieved either by orthogonal vertical and horizontal polarizations or orthogonal left-hand circular and right-hand circular polarizations. 
     When duplicate modem blocks, RF blocks, and PA/LNA/switch blocks are provided in a conventional PTP radio, then connecting each PHY chain to a respective polarization feed of the antenna allows theoretically up to twice the total amount of information to be communicated within a given channel bandwidth to the extent that cross-polarization self-interference can be minimized or cancelled sufficiently. Such a system is said to employ “dual-polarization” signaling. Such systems may be referred to as having two “streams” of information, whereas multiple input multiple output (MIMO) systems utilizing spatial multiplexing may achieve successful communications using even more than two streams in practice. 
     When an additional circuit (not shown) is added to  FIG. 2A  that can provide either the RF Tx signal or its anti-phase equivalent to either one or both of the two polarization feeds of such an antenna, then “cross-polarization” signaling can be used to effectively expand the constellation of the modem within any given symbol rate or channel bandwidth. With two polarizations and the choice of RF signal or its anti-phase, then an additional two information bits per symbol can be communicated across the link. Theoretically, this can be extended and expanded to additional phases, representing additional information bits. At the receiver, for example, a circuit (not shown) could detect if the two received polarizations are anti-phase with respect to each other, or not, and then combine appropriately such that the demodulator in the modem block can determine the absolute phase and hence deduce the values of the two additional information bits. Cross-polarization signaling has the advantage over dual-polarization signaling in that it is generally less sensitive to cross-polarization self-interference but for high order constellations such as 64-QAM or 256-QAM, the relative increase in channel efficiency is smaller. 
     In the conventional PTP radios shown in  FIGS. 2A and 2B , substantially all the components are in use at all times when the radio link is operative. However, many of these components have programmable parameters that can be controlled dynamically during link operation to optimize throughout and reliability for a given set of potentially changing operating conditions. The conventional PTP radios of  FIGS. 2A and 2B  control these link parameters via a Radio Link Controller (RLC)  248 A,  248 B. The RLC functionality is also often described as a Link Adaptation Layer that is typically implemented as a software routine executed on a microcontroller within the radio that can access the MAC  212 A,  212 B, Modem  216 A,  216 B, RF  220 A,  220 B and/or possibly other components with controllable parameters. The RLC  248 A,  248 B typically can both vary parameters locally within its radio and communicate with a peer RLC at the other end of the conventional PTP radio link via “control frames” sent by the MAC  212 A,  212 B with an appropriate identifying field within a MAC Header. 
     Typical parameters controllable by the RLC  248 A,  248 B for the Modem  216 A,  216 B of a conventional PTP radio include encoder type, encoding rate, constellation selection and reference symbol scheduling and proportion of any given PHY Protocol Data Unit (PPDU). Typical parameters controllable by the RLC  248 A,  248 B for the RF  220 A,  220 B of a conventional PTP radio include channel frequency, channel bandwidth, and output power level. To the extent that a conventional PTP radio employs two polarization feeds within its single antenna, additional parameters may also be controlled by the RLC  248 A,  248 B as self-evident from the description above. 
     In conventional PTP radios, the RLC  248 A,  248 B decides, usually autonomously, to attempt such parameter changes for the link in response to changing propagation environment characteristics such as, for example, humidity, rain, snow, or co-channel interference. There are several well-known methods for determining that changes in the propagation environment have occurred such as monitoring the receive signal strength indicator (RSSI), the number of or relative rate of FCS failures at the MAC  212 A,  212 B, and/or the relative value of certain decoder accuracy metrics. When the RLC  248 A,  248 B determines that parameter changes should be attempted, it is necessary in most cases that any changes at the transmitter end of the link become known to the receiver end of the link in advance of any such changes. For conventional PTP radios, and similarly for many other radios, there are at least two well-known techniques which in practice may not be mutually exclusive. First, the RLC  248 A,  248 B may direct the PHY, usually in the Modem  216 A,  216 B relative to  FIGS. 2A and 2B , to pre-pend a PHY layer convergence protocol (PLCP) header to a given PPDU that includes one or more (or a fragment thereof) given MPDUs wherein such PLCP header has information fields that notify the receiving end of the link of parameters used at the transmitting end of the link. Second, the RLC  248 A,  248 B may direct the MAC  212 A,  212 B to send a control frame, usually to a peer RLC  248 A,  248 B, including various information fields that denote the link adaptation parameters either to be deployed or to be requested or considered. 
     The foregoing describes at an overview level the typical structural and operational features of conventional PTP radios which have been deployed in real-world conditions for many radio links where unobstructed (or substantially unobstructed) LOS propagation was possible. The conventional PTP radio on a whole is completely unsuitable for obstructed LOS PTP or PMP operation. 
     More recently, as briefly mentioned, there has been significant adoption of so called multiple input multiple output (MIMO) techniques, which utilizes spatial multiplexing of multiple information streams between a plurality of transmission antennas to a plurality of receive antennas. The adoption of MIMO has been most beneficial in wireless communication systems for use in environments having significant multipath scattering propagation. One such system is IEEE802.11n for use in home networking. Attempts have been made to utilize MIMO and spatial multiplexing in line of sight environments having minimal scattering, which have generally been met with failure, in contrast to the use of cross polarized communications. For example IEEE802.11n based Mesh networked nodes deployed at streetlight elevation in outdoor environments often experience very little benefit from the use of spatial multiplexing due to the lack of a rich multipath propagation environment. Additionally, many of these deployments have limited range between adjacent mesh nodes due to physical obstructions resulting in the attenuation of signal levels. 
     Radios and systems with MIMO capabilities intended for use in both near line of sight (NLOS) and line of sight (LOS) environments are disclosed in U.S. patent application Ser. Nos. 13/212,036, now U.S. Pat. No. 8,238,318, and 13/536,927, both of which are incorporated herein by reference, and are referred to herein by the term “Intelligent Backhaul Radio” (IBR). 
       FIGS. 3A and 3B  illustrate exemplary embodiments of the disclosed IBRs. In  FIGS. 3A and 3B , the IBRs include interfaces  304 A, interface bridge  308 A, MAC  312 A, modem  324 A, channel MUX  328 A, RF  332 A, which includes T×1 . . . T×M  336 A and R×1 . . . R×N  340 A, IBR Antenna Array  348 A (includes multiple antennas  352 A), a Radio Link Controller (RLC)  356 A and a Radio Resource Controller (RRC)  360 A. The IBR may optionally include an “Intelligent Backhaul Management System” (or “IBMS”) agent  370 B as shown in  FIG. 3B . It will be appreciated that the components and elements of the IBRs may vary from that illustrated in  FIGS. 3A and 3B . 
     Embodiments of such intelligent backhaul radios, as disclosed in the foregoing references, include one or more demodulator cores within modem  324 A, wherein each demodulator core demodulates one or more receive symbol streams to produce a respective receive data interface stream; a plurality of receive RF chains  340 A within IBR RF  332 A to convert from a plurality of receive RF signals from IBR Antenna Array  348 A, to a plurality of respective receive chain output signals; a frequency selective receive path channel multiplexer within IBR Channel multiplexer  328 A, interposed between the one or more demodulator cores and the plurality of receive RF chains, to produce the one or more receive symbol streams provided to the one or more demodulator cores from the plurality of receive chain output signals; an IBR Antenna Array ( 348 A) including: a plurality of directive gain antenna elements  352 A; and one or more selectable RF connections that selectively couple certain of the plurality of directive gain antenna elements to certain of the plurality of receive RF chains, wherein the number of directive gain antenna elements that can be selectively coupled to receive RF chains exceeds the number of receive RF chains that can accept receive RF signals from the one or more selectable RF connections; and a radio resource controller, wherein the radio resource controller sets or causes to be set the specific selective couplings between the certain of the plurality of directive gain antenna elements and the certain of the plurality of receive RF chains. 
     The intelligent backhaul radio may further include one or more modulator cores within IBR Modem  324 A, wherein each modulator core modulates a respective transmit data interface stream to produce one or more transmit symbol streams; a plurality of transmit RF chains  336 A within IBR RF  332 A, to convert from a plurality of transmit chain input signals to a plurality of respective transmit RF signals; a transmit path channel multiplexer within IBR Channel MUX  328 A, interposed between the one or more modulator cores and the plurality of transmit RF chains, to produce the plurality of transmit chain input signals provided to the plurality of transmit RF chains from the one or more transmit symbol streams; and, wherein the IBR Antenna Array  348 A further includes a plurality of RF connections to couple at least certain of the plurality of directive gain antenna elements to the plurality of transmit RF chains. 
     The primary responsibility of the RLC  356 A in exemplary intelligent backhaul radios is to set or cause to be set the current transmit “Modulation and Coding Scheme” (or “MC S”) and output power for each active link. For links that carry multiple transmit streams and use multiple transmit chains and/or transmit antennas, the MCS and/or output power may be controlled separately for each transmit stream, chain, or antenna. In certain embodiments, the RLC operates based on feedback from the target receiver for a particular transmit stream, chain and/or antenna within a particular intelligent backhaul radio. 
     The intelligent backhaul radio may further include an intelligent backhaul management system agent  370 B that sets or causes to be set certain policies relevant to the radio resource controller, wherein the intelligent backhaul management system agent exchanges information with other intelligent backhaul management system agents within other intelligent backhaul radios or with one or more intelligent backhaul management system servers. 
       FIG. 3C  illustrates an exemplary embodiment of an IBR Antenna Array  348 A.  FIG. 3C  illustrates an antenna array having Q directive gain antennas  352 A (i.e., where the number of antennas is greater than 1). In  FIG. 3C , the IBR Antenna Array  348 A includes an IBR RF Switch Fabric  312 C, RF interconnections  304 C, a set of Front-ends  308 C and the directive gain antennas  352 A. The RF interconnections  304 C can be, for example, circuit board traces and/or coaxial cables. The RF interconnections  304 C connect the IBR RF Switch Fabric  312 C and the set of Front-ends  308 C. Each Front-end  308 C is associated with an individual directive gain antenna  352 A, numbered consecutively from 1 to Q. 
       FIG. 3D  illustrates an exemplary embodiment of the Front-end circuit  308 C of the IBR Antenna Array  348 A of  FIG. 3C  for the case of TDD operation, and  FIG. 3E  illustrates an exemplary embodiment of the Front-end circuit  308 C of the IBR Antenna Array  348 A of  FIG. 3C  for the case of FDD operation. The Front-end circuit  308 C of  FIG. 3E  includes a transmit power amplifier PA  304 D, a receive low noise amplifier LNA  308 D, SPDT switch  312 D and band-select filter  316 D. The Front-end circuit  308 C of  FIG. 3E  includes a transmit power amplifier PA  304 E, receive low noise amplifier LNA  308 E, and duplexer filter  312 E. These components of the Front-end circuit are substantially conventional components available in different form factors and performance capabilities from multiple commercial vendors. 
     As shown in  FIGS. 3D and 3E , each Front-end  308 E also includes an “Enable” input  320 D,  320 E that causes substantially all active circuitry to power-down. Power-down techniques are well known. Power-down is advantageous for IBRs in which not all of the antennas are utilized at all times. It will be appreciated that alternative embodiments of the IBR Antenna Array may not utilize the “Enable” input  320 D,  320 E or power-down feature. Furthermore, for embodiments with antenna arrays where some antenna elements are used only for transmit or only for receive, then certain Front-ends (not shown) may include only the transmit or only the receive paths of  FIGS. 3D and 3E  as appropriate. 
       FIG. 3F  illustrates an alternative embodiment of an IBR Antenna Array  348 A and includes a block diagram of an IBR antenna array according to one embodiment of the invention relating to the use of dedicated transmission and reception antennas. In some IBR embodiments the embodiment of  FIG. 3C  may be replaced with the embodiments described in relation to  FIG. 3F . For instance, such substitution may be made in use with either FDD, TDD, or even non-conventional duplexing systems.  FIG. 3F  illustrates an antenna array having Q R +Q T  directive gain antennas  352 A (i.e., where the number of antennas is greater than 1). In  FIG. 3F , the IBR Antenna Array  348 A includes an IBR RF Switch Fabric  312 F, RF interconnections  304 C, a set of Front-ends  309 F and  310 F and the directive gain antennas  352 A. The RF interconnections  304 C can be, for example, circuit board traces and/or coaxial cables. The RF interconnections  304 C connect the IBR RF Switch Fabric  312 F and the set of Front-end Transmission Units  309 F and the set of Front-end Reception Units  310 F. Each Front-end transmission unit  309 F is associated with an individual directive gain antenna  352 A, numbered consecutively from 1 to Q T . Each Front-end reception unit  310 F is associated with an individual directive gain antenna  352 A, numbered consecutively from 1 to Q R . The present embodiment may be used, for example, with the antenna array embodiments of  FIG. 3I, 3J , or embodiments described elsewhere. Such dedicated transmission antennas are coupled to front-end transmission units  309 F and include antenna element  352 A. 
     In alternative embodiment, the IBR RF Switch fabric  312 F may be bypassed for the transmission signals when the number of dedicated transmission antennas and associated front-end transmission units (Q T ) is equal to the number of RF transmission signals RF-Tx-M (e.g. Q T =M), resulting in directly coupling the IBR RF  336 A transmissions to respective transmission front-end transmission units  309 F. The dedicated reception antennas, including an antenna element  352 A in some embodiments, are coupled to front-end reception units  310 F, which in the present embodiment are coupled to the IBR RF Switch Fabric. In an additional alternative embodiment, the IBR RF Switch fabric  312 F may be bypassed for the reception signals when the number of dedicated reception antennas and associated front-end reception units (Q R ) is equal to the number of RF reception signals RF-Rx-N (e.g. Q R =N), resulting in directly coupling the IBR RF  340 A reception ports to respective front-end reception units  310 F. 
       FIG. 3G  is a block diagram of a front-end transmission unit according to one embodiment of the invention relating to the use of dedicated transmission and reception antennas, and  FIG. 3H  is a block diagram of a front-end reception unit according to one embodiment of the invention relating to the use of dedicated transmission and reception antennas. As shown in  FIGS. 3G and 3H , each Front-end  309 F and  310 F also includes a respective “Enable” input  325 F,  330 F that causes substantially all respective active circuitry to power-down, and any known power-down technique may be used. Power-down is advantageous for IBRs in which not all of the antennas are utilized at all times. It will be appreciated that alternative embodiments of the IBR Antenna Array may not utilize the “Enable” input  325 F,  330 F or any power-down feature. Furthermore, for some embodiments associated with  FIG. 3F  for example (with antenna arrays where some antenna elements are used only for transmit or only for receive) then certain Front-ends may include only the transmit  309 F or only the receive paths  310 F of  FIGS. 3G and 3H  as appropriate. With respect to  FIG. 3G , Bandpass filter  340 G receives transmission signal RF-SW-Tx-qt, provides filtering and couples the signal to power amplifier  304 G, then to low pass filter  350 G. The output of the lowpass filter is then coupled to dedicated transmission antenna, which includes directive antenna element  352 A. With respect to  FIG. 3H , directive antenna element  352 A is a dedicated receive only antenna and coupled to receive filter  370 H, when is in turn coupled to LNA  308 H. The resulting amplified receive signal is coupled to band bass filter  360 H, which provides output RF-SW-Rx-qr. 
     As described above, each Front-end (FE-q) corresponds to a particular directive gain antenna  352 A. Each antenna  352 A has a directivity gain Gq. For IBRs intended for fixed location street-level deployment with obstructed LOS between IBRs, whether in PTP or PMP configurations, each directive gain antenna  352 A may use only moderate directivity compared to antennas in conventional PTP systems at a comparable RF transmission frequency. 
     As described in greater detail in U.S. patent application Ser. Nos. 13/212,036, now U.S. Pat. No. 8,238,318, and 13/536,927 and incorporated herein by reference, various antenna configurations may be utilized in point-to-point and point-to-multipoint embodiments of the current invention. With reference to  FIG. 3I , a block diagram of an exemplary IBR antenna array is depicted. Such an array may also be used in part or in entirety as a receive and/or transmit antenna array for an IBR device according to one embodiment of the invention. As the array includes a plurality of antenna panels ( 3101 -A . . . D,  3301 , for example), each panel may include one of the antenna structures or individual antennas including the antenna structures. In an IBR device, normally two such antenna arrays including some or all of the antenna panels depicted in  FIG. 3I  would be utilized with an azimuthal directional bias different for each array or for each collection of one or more such antenna panels to optimize link performance between the instant IBR and the source and destination devices. 
     While  FIG. 3I  is a diagram of an exemplary horizontally arranged intelligent backhaul radio antenna array,  FIG. 3J  is a diagram of an exemplary vertically arranged intelligent backhaul radio antenna array that may also be used in part or in entirety as a receive and/or transmit antenna array for an IBR device according to one embodiment of the invention. The depicted antenna arrays shown in  FIGS. 3I and 3J  are intended for operation in the 5 to 6 GHz band. Analogous versions of the arrangement shown in FIGS.  3 I and  3 J are possible for any bands within the range of at least 500 MHz to 100 GHz as will be appreciated by those of skill in the art of antenna design. 
     The exemplary transmit directive antenna elements depicted in  FIGS. 3I and 3J  include multiple dipole radiators arranged for either dual slant 45 degree polarization ( FIG. 3I ) or dual vertical and horizontal polarization ( FIG. 3J ) with elevation array gain as described in greater detail in U.S. patent application Ser. No. 13/536,927 and incorporated herein. In one exemplary embodiment, each transmit directive antenna element has an azimuthal beam width of approximately 100-120 degrees and an elevation beam width of approximately 15 degrees for a gain Gqt of approximately 12 dB. 
     The receive directive antenna elements depicted in  FIGS. 3I and 3J  include multiple patch radiators arranged for either dual slant 45 degree polarization or dual vertical and horizontal polarization with elevation array gain and azimuthal array gain as described in greater detail in U.S. patent application Ser. No. 13/536,927 and incorporated herein. In one exemplary embodiment, each receive directive antenna element has an azimuthal beam width of approximately 40 degrees and an elevation beam width of approximately 15 degrees for a gain Gqr of approximately 16 dB. 
     Preliminary measurements of exemplary antenna arrays similar to those depicted in  FIG. 3I  show isolation of approximately 40 to 50 dB between individual transmit directive antenna elements and individual receive directive antenna elements of same polarization with an exemplary circuit board and metallic case behind the radiating elements and a plastic ray dome in front of the radiating elements. Analogous preliminary measurements of exemplary antenna arrays similar to those depicted in FIG.  3 J show possible isolation improvements of up to 10 to 20 dB for similar directive gain elements relative to  FIG. 3I . 
     Other directive antenna element types are also known to those of skill in the art of antenna design including certain types described in greater detail in U.S. patent application Ser. No. 13/536,927 and incorporated herein. 
     In the exemplary IBR Antenna Array  348 A illustrated in  FIG. 3A  through  FIG. 3J , the total number of individual antenna elements  352 A, Q, is greater than or equal to the larger of the number of RF transmit chains  336 A, M, and the number of RF receive chains  340 A, N. In some embodiments, some or all of the antennas  352 A may be split into pairs of polarization diverse antenna elements realized by either two separate feeds to a nominally single radiating element or by a pair of separate orthogonally oriented radiating elements. Such cross polarization antenna pairs enable either increased channel efficiency or enhanced signal diversity as described for the conventional PTP radio. The cross-polarization antenna pairs as well as any non-polarized antennas are also spatially diverse with respect to each other. Additionally, the individual antenna elements may also be oriented in different directions to provide further channel propagation path diversity. 
     The foregoing discussion related to intelligent backhaul radios and relate diagrams have include the use of frequency division duplexing (FDD) and time division duplexing (TDD) techniques and architectures. Such architectures, as discussed, include support of both single input and single output (SISO) supporting single stream operation, and multiple input/multiple output (MIMO) multiple stream operation support. Additional embodiments supporting SISO and MIMO technology in specific embodiments include the use so-called zero division duplexed (ZDD) intelligent backhaul radios (ZDD-IBR), as disclosed in U.S. patent application Ser. No. 13/609,156, now U.S. Pat. No. 8,422,540, which is additionally incorporated herein by reference. 
     Embodiments of the ZDD systems provide for the operation of a IBR wherein the ZDD-IBR transmitter and receiver frequencies are close in frequency to each other so as to make the use of frequency division duplexing, as known in the art, impractical. Arrangements of ZDD operation disclosed in the foregoing referenced application include so-called “co-channel” embodiments wherein the transmit frequency channels in use by a ZDD-IBR, and the receive frequencies are partially or entirely overlapped in the frequency spectrum. Additionally disclosed embodiments of ZDD-IBRs include so-called “co-band” ZDD operation wherein the channels of operation of the ZDD-IBR are not directly overlapped with the ZDD-IBR receive channels of operation, but are close enough to each other so as to limit the performance the system. For example, at specific receiver and transmitter frequency channel separation, the frequency selectivity of the channel selection filters in an IBR transmitter and receiver chains may be insufficient to isolate the receiver(s) from the transmitter signal(s) or associated noise and distortion, resulting in significant de-sensitization of the IBR&#39;s receiver(s) performance at specific desired transmit power levels, with out the use of disclosed ZDD techniques. Embodiments of the disclosed ZDD-IBRs include the use of radio frequency, intermediate frequency and base band cancelation of reference transmitter and interference signals from the ZDD-IBR receivers in a MIMO configuration. Such disclosed ZDD techniques utilize the estimation of the channels from the plurality of IBR transmitters to the plurality of IBR receivers of the same intelligent backhaul radio, and the adaptive filtering of the reference signals based upon the channel estimates so as to allow the cancelation the transmitter signals from the receivers utilizing such estimated cancelation signals. Such ZDD techniques allow for increased isolation between the desired receive signals and the ZDD-IBR&#39;s transmitters in various embodiments including MIMO (and SISO) configurations. 
     The support for MIMO operation (FDD, TDD, or ZDD) is highly dependent upon the radio propagation environment between the two radios in communication with each other. The following discussion provides for a general discussion relating to the MIMO channel, and will provide a basis for further discussion. Referring now to  FIG. 3K-A  the MIMO channel matrix is depicted. Transceiver MIMO Station  3 K- 05  is in communication with MIMO Station  3 K- 10  utilizing MIMO channel matrix (Eq. 3K-1) of  FIG. 3K-B  between the 2 stations of  FIG. 3K-A . In an example of a two-by-two MIMO system, two spatial streams are utilized between the two MIMO stations. The channel propagation matrix of Eq. 3K-1 is of order M by N (M rows and N columns). A particular element of the channel propagation matrix, him, represents the frequency response of the wireless channel from the n th  transmitter to the m th  receiver. Therefore each element of the channel propagation matrix H has an individual complex number, if the channel is “frequency flat,” or a complex function of frequency, if the channel is “frequency selective,” which represents the amplitude and phase of the propagation channel between one transmitter and one receiver of MIMO Stations  3 K- 05  and  3 K- 10 . Often, the channel propagation matrix and the individual propagation coefficients are frequency selective, meaning that the complex value of the coefficients vary as a function of frequency as mentioned. In a rich, multipath scattering environment, as depicted in  FIG. 3L , in which sufficient signal strength reaches an intended receiver but is scattered amongst the various structures between a particular MIMO transmitter and MIMO receiver, the spatial distribution of the arriving signals is referred to as a rich multipath environment in which there is a significant angular scattering among the receiving signals at the intended receiver. 
     In order to separate the MIMO streams received at an intended receiver, such as MIMO Station  3 K- 05  or MIMO Station  3 K- 10 , the channel propagation matrix H must be determined, as known in the art. The process of determining the channel propagation matrix is often performed utilizing pilot channels, preambles, and/or symbols or other known reference information. Examples of prior art systems utilizing such techniques include IEEE 802.11n, LTE, or HSPA, as well as various embodiments of intelligent backhaul radios per U.S. Pat. Nos. 8,238,818, 8,422,540 and U.S. patent application Ser. No. 13/536,927 as incorporated in their entireties herein. 
     In order for MIMO systems (including the foregoing mentioned MIMO systems) to support a plurality of spatial MIMO streams, the order of the propagation matrix (referenced as Eq. 3K-1) must equal or exceed the desired number of streams. While this condition is necessary, it is not sufficient. The rank of the matrix must also equal or exceed the number of desired spatial streams. The rank of a matrix is the maximum number of linearly independent column vectors of the propagation matrix. Such terminology is known in the art with respect to linear algebra. The number of supportable MIMO streams must be less than or equal to the rank of the channel propagation matrix. When the propagation coefficients from multiple transmitters of a MIMO station to a plurality of intended receive antennas are correlated, the number of linearly independent column vectors of the channel propagation matrix H is reduced and consequently the system will support fewer MIMO streams. Such a condition often occurs in environments where a small angular spread at the desired intended receiver is present, such as is the case with a line-of-sight environment where the two MIMO stations are a significant distance apart, such that the angular resolution of the receiving antennas at MIMO Station  3 K- 10  is insufficient to resolve and separate the signals transmitted from the plurality of transmitters at MIMO Station  3 K- 05 . Such a condition is referred to as an ill-conditioned channel matrix for the desired number of streams in the MIMO system, due to the rank of the channel propagation matrix (i.e. the number of linearly independent column vectors) being less than the desired number of MIMO streams between the two MIMO stations. The reasoning behind the rank of the channel propagation matrix being required to be greater than or equal to the desired number of MIMO streams is related to how the individual streams are separated from one another at the intended receiving MIMO station. As is known in the art, the MIMO performance is quite sensitive to the invertability of the channel propagation matrix. Such invertability, as previously mentioned, may be compromised by the receiving antenna correlation, which may be caused by close antenna spacing or small angular spread at the intended MIMO receiver. The line-of-sight condition between two MIMO stations may result in such a small angular spread between the MIMO receivers, resulting in the channel matrix being noninvertible or degenerate. Multipath fading, which often results from large angular spreads amongst individual propagation proponents between two antennas, enriches the condition of the channel propagation matrix, making the individual column vectors linearly independent and allowing the channel propagation matrix to be invertible. The inversion of the channel propagation matrix results in weights (vectors), which are utilized with the desired receive signals to separate the linear combination of transmitted streams into individual orthogonal streams, allowing for proper reception of each individual stream from spatially multiplexed composite information streams. In a line-of-sight environment, all of the column vectors of the channel propagation matrix H may be highly correlated, resulting in a matrix rank of 1 or very close to 1. Such a matrix is noninvertible and ill-conditioned, resulting in the inability to support spatial multiplexing and additional streams (other than by the use of polarization multiplexing, which provides for only 2 streams as discussed). 
       FIG. 3L  illustrates an exemplary deployment of intelligent backhaul radios (IBRs). As shown in  FIG. 3L , the IBRs  300 L are deployable at street level with obstructions such as trees  303 L, hills  308 L, buildings  312 L, etc. between them. Embodiments of intelligent backhaul radios (IBRs) are discussed in co-pending US patent application Ser. Nos. 13/212,036, now U.S. Pat. No. 8,238,318, and 13/536,927, the entire contents of which is incorporated herein. The IBRs  300 L are also deployable in configurations that include point-to-multipoint (PMP), as shown in  FIG. 3L , as well as point-to-point (PTP). In other words, each IBR  300 L may communicate with more than one other IBR  300 L. 
     For 3G and especially for 4 th  Generation (4G), cellular network infrastructure is more commonly deployed using “microcells” or “picocells.” In this cellular network infrastructure, compact base stations (eNodeBs)  316 L are situated outdoors at street level. When such eNodeBs  316 L are unable to connect locally to optical fiber or a copper wireline of sufficient data bandwidth, then a wireless connection to a fiber “point of presence” (POP) requires obstructed LOS capabilities, as described herein. 
     For example, as shown in  FIG. 3L , the IBRs  300 L include an Aggregation End IBR (AE-IBR) and Remote End IBRs (RE-IBRs). The eNodeB  316 L of the AE-IBR is typically connected locally to the core network via a fiber POP  320 L. The RE-IBRs and their associated eNodeBs  316 L are typically not connected to the core network via a wireline connection; instead, the RE-IBRs are wirelessly connected to the core network via the AE-IBR. As shown in  FIG. 3L , the wireless connection between the IBRs include obstructions (i.e., there may be an obstructed LOS connection between the RE-IBRs and the AE-IBR). Note that the Tall Building  312 L substantially impedes the signal transmitted from RE-IBR  300 L to AR-IBR  300 L. Additionally, in at least one example scenario, the tree ( 303 L) provides unacceptable signal attenuation between an RE-IBR  300 L and the AE-IBR  300 L. 
     As discussed above, the advances in cellular communications, and more specifically the Third Generation Partnership Program&#39;s (3GPP, www.3GPP.org) Long Term Evolution (LTE), and associated cellular “off load” use of IEEE 802.11 communication protocols continues to drive the data backhaul requirements of cellular infrastructure sites to ever increasing levels. The need for an increasing number of wireless backhaul links to satisfy the cellular backhaul demand demands the use of potentially congested wireless spectrum resources. 
     The Federal Communications Commission (FCC) has allowed for the use of currently licensed broadcast television spectrum for use by unlicensed devices. This program has been commonly referred to as the “TV Whitespaces” reuse (http://www.fcc.gov/topic/white-space). A detailed description of the program is provided in FCC order FCC-10-174A1, and the rules for unlicensed devices that operate in the TV bands are set forth in 47 C.F.R. §§ 15.701-.717. See TITLE 47—Telecommunication; CHAPTER I—FEDERAL COMMUNICATIONS COMMISSION; SUBCHAPTER A—GENERAL, PART 15—RADIO FREQUENCY DEVICES, Subpart H—TELEVISION BAND DEVICES (http://www.ecfr.gov/cgi-bin/text-idx?c=ecfr&amp; SID=30f46f0753577b10de41d650c7adf941&amp;rgn=div6&amp;view=text&amp;node=4 7:1.0.1.1.16.8&amp;idno=47). 
     The TV Whitespaces program provides for a reuse of underutilized spectrum resources for public use by unlicensed devices (TV Band Devices). Further, so-called “Incumbent Services” remain protected from interference from the TV Band Devices (TVBDs) by a set of operating rules and concepts including (selectively extracted from CFR 47 § 15.703 Definitions.):
         (a) Available channel. A six-megahertz television channel, which is not being used by an authorized service at or near the same geographic location as the TVBD and is acceptable for use by an unlicensed device under the provisions of this subpart.   (b) Contact verification signal. An encoded signal broadcast by a fixed or Mode II device for reception by Mode I devices to which the fixed or Mode II device has provided a list of available channels for operation. Such signal is for the purpose of establishing that the Mode I device is still within the reception range of the fixed or Mode II device for purposes of validating the list of available channels used by the Mode I device and shall be encoded to ensure that the signal originates from the device that provided the list of available channels. A Mode I device may respond only to a contact verification signal from the fixed or Mode II device that provided the list of available channels on which it operates. A fixed or Mode II device shall provide the information needed by a Mode I device to decode the contact verification signal at the same time it provides the list of available channels.   (c) Fixed device. A TVBD that transmits and/or receives radiocommunication signals at a specified fixed location. A fixed TVBD may select channels for operation itself from a list of available channels provided by a TV bands database, initiate and operate a network by sending enabling signals to one or more fixed TVBDs and/or personal/portable TVBDs. Fixed devices may provide to a Mode I personal/portable device a list of available channels on which the Mode I device may operate under the rules, including available channels above 512 MHz (above TV channel 20) on which the fixed TVBD also may operate and a supplemental list of available channels above 512 MHz (above TV channel 20) that are adjacent to occupied TV channels on which the Mode I device, but not the fixed device, may operate.   (d) Geo-location capability. The capability of a TVBD to determine its geographic coordinates within the level of accuracy specified in § 15.711(b)(1), i.e. 50 meters. This capability is used with a TV bands database approved by the FCC to determine the availability of TV channels at a TVBD&#39;s location.   (e) Mode I personal/portable device. A personal/portable TVBD that does not use an internal geo-location capability and access to a TV bands database to obtain a list of available channels. A Mode I device must obtain a list of available channels on which it may operate from either a fixed TVBD or Mode II personal/portable TVBD. A Mode I device may not initiate a network of fixed and/or personal/portable TVBDs nor may it provide a list of available channels to another Mode I device for operation by such device.   (f) Mode II personal/portable device. A personal/portable TVBD that uses an internal geo-location capability and access to a TV bands database, either through a direct connection to the Internet or through an indirect connection to the Internet by way of fixed TVBD or another Mode II TVBD, to obtain a list of available channels. A Mode II device may select a channel itself and initiate and operate as part of a network of TVBDs, transmitting to and receiving from one or more fixed TVBDs or personal/portable TVBDs. A Mode II personal/portable device may provide its list of available channels to a Mode I personal/portable device for operation on by the Mode I device.   (g) Network initiation. The process by which a fixed or Mode II TVBD sends control signals to one or more fixed TVBDs or personal/portable TVBDs and allows them to begin communications.   (h) Operating channel. An available channel used by a TVBD for transmission and/or reception.   (i) Personal/portable device. A TVBD that transmits and/or receives radiocommunication signals at unspecified locations that may change. Personal/portable devices may only transmit on available channels in the frequency bands 512-608 MHz (TV channels 21-36) and 614-698 MHz (TV channels 38-51).   (j) Receive site. The location where the signal of a full service television station is received for rebroadcast by a television translator or low power TV station, including a Class A TV station, or for distribution by a Multiple Video Program Distributor (MVPD) as defined in 47 U.S.C. 602(13).   (k) Sensing only device. A personal/portable TVBD that uses spectrum sensing to determine a list of available channels. Sensing only devices may transmit on any available channels in the frequency bands 512-608 MHz (TV channels 21-36) and 614-698 MHz (TV channels 38-51).   (1) Spectrum sensing. A process whereby a TVBD monitors a television channel to detect whether the channel is occupied by a radio signal or signals from authorized services.   (m) Television band device (TVBD). Intentional radiators that operate on an unlicensed basis on available channels in the broadcast television frequency bands at 54-60 MHz (TV channel 2), 76-88 MHz (TV channels 5 and 6), 174-216 MHz (TV channels 7-13), 470-608 MHz (TV channels 14-36) and 614-698 MHz (TV channels 38-51).   (n) TV bands database. A database system that maintains records of all authorized services in the TV frequency bands, is capable of determining the available channels as a specific geographic location and provides lists of available channels to TVBDs that have been certified under the Commission&#39;s equipment authorization procedures. TV bands databases that provide lists of available channels to TVBDs must receive approval by the Commission.       

     Under the white spaces rules, TVBDs (other than TVBDs that rely on spectrum sensing) have the requirement of registering with the TV bands database, and determining available channels of operation. This process requires providing the database the FCC ID, serial number, geographic location, and other information to the database, to receive a list of available channels for operation. TVBDs are further required to periodically re-register with the database to re-determine available channels of operation. An example of a database entry information for a Fixed TVDB is provided within CFR 47 § 15.713 TV bands database (f) Fixed TVBD registration (extraction follows).
         (1) Prior to operating for the first time or after changing location, a fixed TVBD must register with the TV bands database by providing the information listed in paragraph (f)(3) of this section.   (2) The party responsible for a fixed TVBD must ensure that the TVBD registration database has the most current, up-to-date information for that device.   (3) The TVBD registration database shall contain the following information for fixed TVBDs:
           (i) FCC identifier (FCC ID) of the device;   (ii) Manufacturer&#39;s serial number of the device;   (iii) Device&#39;s geographic coordinates (latitude and longitude (NAD 83) accurate to ±/−50 m);   (iv) Device&#39;s antenna height above ground level (meters);   (v) Name of the individual or business that owns the device;   (vi) Name of a contact person responsible for the device&#39;s operation;   (vii) Address for the contact person;   (viii) E-mail address for the contact person;   (ix) Phone number for the contact person.   
               

     The foregoing is intended to provide a brief overview of the concepts and rules associated with the TV White spaces device operation. 
     While suitable for use by some wireless applications, such a system is not ideal for use in many highly reliable wireless backhaul applications. As one example, the lack of protection from interference for TVBD registered devices is a significant impediment for achieving a highly reliable data link for backhaul applications in view of interference from unlicensed or other wireless devices, including other TVBD devices. As another example, there is no approach for devices to arbitrate interference amongst one another. There are significant number of other deficiencies of the TV white spaces rules making them non-ideal for use in other bands, and in other applications of use such as cellular backhaul. 
     SUMMARY 
     The following summary of the invention is included in order to provide a basic understanding of some aspects and features of the invention. This summary is not an extensive overview of the invention and as such it is not intended to particularly identify key or critical elements of the invention or to delineate the scope of the invention. Its sole purpose is to present some concepts of the invention in a simplified form as a prelude to the more detailed description that is presented below. 
     Various embodiments of the present invention provide for incorporation of a “Tiered” group of devices and/or licenses associated with providing a hierarchical set of interference protection mechanisms for members of each tier of service in a wireless backhaul (or other) application. Exemplary systems, devices, and methods are disclosed in various embodiments to allow for the efficient operation of such a tiered service. As previously described, the TV Whitespaces rules do not provide for mechanisms or devices allowing for such an efficient tiered service. Embodiments of the invention provide a tiered service which allows for interference protection among devices belonging to one or more tiers of the service, from other devices within the same tier of service, or other tiers of service. Embodiments of the invention include mechanisms, apparatus, and methods that provide for the identification of other devices of the same or differing tier of service, and mitigate interference to or from the device based upon intercommunication between the devices, and/or via a central registry database. 
     According to other aspects of the invention, a first tiered service radio is disclosed for operating in a radio frequency band according to rules for operation allowing for radios of multiple tiers of service, including a plurality of receive RF chains; one or more transmit RF chains; an antenna array having a plurality of directive gain antenna elements, wherein each directive gain antenna element is couplable to at least one receive RF or transmit RF chain; and an interface bridge configured to couple the radio to a data network; wherein the tiered service radio is configured to perform each of the following: communicate with a network based registry to determine registry information associated with any registered radios meeting specific criteria, wherein the specific criteria includes at least information associated with at least higher priority tiered service radio devices to that of the first tiered service radio; scan one or more radio frequency channels for the presence of signature radio signals transmitted from one or more other tiered service radios to generate scan data, and wherein the radio includes at least one adjustable network parameter that is adjustable based on the scan data, wherein said scanned one or more radio frequency channels are selected based upon said registry information, and wherein the at least one network parameter is adjusted to reduce a potential of interference of the first tiered service radio with both the other tiered service radios or said registered radios, wherein the adjusting the at least one network parameter includes one or more of: selecting a frequency channel utilized between the first tiered service radio and a second tiered service radio; adjusting the effective radiation pattern of the first tiered service radio; selecting one or more of the plurality of directive gain antenna elements; and adjusting the physical configuration or arrangement of the one or more of the plurality of directive gain antenna elements. 
     In some embodiments, the tiered service radio is further configured to generate a scan report based on the scan data and transmit the scan report to a server. 
     In some embodiments, the signals include a signal licensed by the Federal Communications Commission (FCC) under service having at least three tiers of service, wherein said tiers include at least legacy point to point backhaul devices at the highest tier and listed in said registry, registered and licensed devices at a second tier, and unlicensed and registered devices at a third and lower tier. 
     In some embodiments, the adjusting the effective radiation pattern includes one or more of: steering the effective radiation pattern in elevation; and steering the effective radiation pattern in azimuth. 
     In some embodiments, the adjusting the effective radiation pattern includes: calculating digital beam former weights based upon at least one constraint related to the potential of interference; and applying the digital beam former weights. 
     In some embodiments, the constraint is selected from the group consisting of: properties related to or derived from said scan result; a direction in which signal transmission is to be limited; parameters which reduce the potential for interfering with one or more of said registered radios meeting said specific criteria; parameters which increase the likelihood of said first and said second tiered service radios meeting performance goals with respect to an interposed wireless communication link; a restriction of use of specific transceivers or specific antennas of a plurality of transceivers or antennas; a use of specific polarizations for transmission; attributes of a collective transmission radiation pattern associated with a plurality of transmitters; a frequency or geometric translation of beam forming weights between receiver weights and transmitter weights; a change in antennas used or selected; a change in operating frequency; and combinations thereof. In some embodiments, the scan report includes one more selected from the group consisting of: the location of said first tiered service radio; the latitude and longitudinal coordinates of one or more tiered service radios; configuration information related to the first tiered service radio; capability information related to the first tiered service radio; a transmission power capability of said first tiered service radio; operating frequency capability of said first tiered service radio; antenna property information related to one or more antenna for use in reception or transmission by said first tiered service radio; received signal parameters or demodulated information from another tiered service radio; received signal parameters from a tiered service radio; and combinations thereof. 
     In some embodiments, the tiered service radio is further configured to assess performance after adjustment of the at least one adjustable network parameter. 
     In some embodiments, the performance of said first tiered service radio is assessed by one or more selected from the group consisting of: performing additional scans; performing additional scans with specific search criteria; performing additional scans with limitations in frequency, azimuth, elevation, or time; performing additional scans with a modified antenna selection configuration; performing additional scans using antennas intended for transmission during normal operation for reception during the additional scanning process; performing transmission of a signal from the first tiered service radio to the second tiered service radio; receiving a signal from the second tiered service radio by the first tiered service radio. 
     In some embodiments, the first tiered service radio is configured to align the antenna array with the second tiered service radio prior to the scan based on at least one criterion. 
     In some embodiments, the at least one criterion is based at least in part upon a signal transmitted from the second tiered service radio. 
     In some embodiments, the at least one criterion includes a GPS location and a compass direction. 
     In some embodiments, the specific criteria includes a geographic region. 
     In some embodiments, the specific criteria includes a tier of service of the first tiered service radio. 
     In some embodiments, the specific criteria includes a date on which service commenced for any tiered service radio registered in the registry. 
     In some embodiments, at least one of said signature radio signals transmitted from the one or more tiered service radios are transmitted inline with information symbols in time from at least one of the tiered service radios. 
     In some embodiments, at least one of said signature radio signals transmitted from the one or more tiered service radios are transmitted as a spread spectrum signal embedded within and simultaneously with information symbols in time from at least one of the tiered service radios. 
     In some embodiments, the first tiered service radio transmits a signature radio signal as a first signature during operation with second tiered service radios. 
     In some embodiments, the first signature is transmitted inline with information symbols in time. 
     In some embodiments, the first signature is transmitted as a spread spectrum signal embedded within and simultaneously with information symbols. 
     In some embodiments, the transmitted first signature is transmitted with progressively increasing interference potential for a period of time prior to initiation of full operation between the first and second tiered service radios. 
     In some embodiments, the progressively increasing interference includes transmission at a power level with an increasing duty cycle over successive periods of time. 
     In some embodiments, the progressively increasing interference includes transmission at several increasing power levels over successive periods of time. 
     In some embodiments, the first tiered service radio alters said at least one network parameter based upon detecting information within said registry or otherwise receiving information informing of detected interference related to the transmitted first signature. 
     In some embodiments, one or more of said other tiered service radios is respectively also one or more of the registered radios meeting the specific criteria. 
     In some embodiments, the scan data includes one or more of the following: information derived form the reception of signature radio signals; information derived from the reception of signals transmitted from said other tiered service radios; information derived from radios other than tiered service radios; received signal strength information; channel propagation information; tiered service radio identity information; angle of arrival of signal information; received signal strength information, interference information; path loss information; and signal transmission periodicity information. 
     In some embodiments, said registered radios include devices of the same priority as the first tiered service radio. 
     In some embodiments, the registered radios include devices of lesser priority as the first tiered service radio. 
     In some embodiments, the registered radios include devices of any tier or any priority as the first tiered service radio. 
     In some embodiments, the specific criterion additionally includes devices of the same priority as the first tiered service radio. 
     In some embodiments, the specific criterion additionally includes devices of lesser priority as the first tiered service radio. 
     In some embodiments, the specific criterion additionally includes devices of any tier or any priority as the first tiered service radio. 
     In some embodiments, the scan is performed including a common control channel, said common control channel being a defined channel for signature radio signal transmission and reception commonly known to a group of tiered service radios upon interaction with the registry. 
     In some embodiments, said specific search criteria includes one or more of the following: information derived form the reception of signature radio signals, information derived from the reception of signals transmitted from said other tiered service radios, information derived from radios other than tiered service radios, received signal strength information, channel propagation information, tiered service radio identity information, angle of arrival of signal information, received signal strength information, interference information, path loss information, and signal transmission periodicity information. 
     Additional embodiments of the current invention, together with the forgoing embodiments, or individually include the use of Advanced Backhaul Services (ABS) devices with point-to-point and point-to-multipoint radios, such as an IBR, as disclosed in U.S. patent application Ser. Nos. 13/212,036, now U.S. Pat. No. 8,238,318, and 13/536,927, the entireties of which are hereby incorporated by reference. Additionally, further embodiments individually, or in combination with forgoing embodiments include the use of ABS devices with so-called zero division duplexed (ZDD) intelligent backhaul radios (ZDD-IBR), as disclosed in U.S. patent application Ser. No. 13/609,156, now U.S. Pat. No. 8,422,540, the entirety of which is hereby incorporated by reference. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       The accompanying drawings, which are incorporated into and constitute a part of this specification, illustrate one or more examples of embodiments and, together with the description of example embodiments, serve to explain the principles and implementations of the embodiments. 
         FIG. 1  is an illustration of conventional point-to-point (PTP) radios deployed for cellular base station backhaul with unobstructed line of sight (LOS). 
         FIG. 2A  is a block diagram of a conventional PTP radio for Time Division Duplex (TDD). 
         FIG. 2B  is a block diagram of a conventional PTP radio for Frequency Division Duplex (FDD). 
         FIG. 3A  is an exemplary block diagram of an IBR. 
         FIG. 3B  is an alternative exemplary block diagram of an IBR. 
         FIG. 3C  is an exemplary block diagram of an IBR antenna array. 
         FIG. 3D  is an exemplary block diagram of a front-end unit for TDD operation of an IBR. 
         FIG. 3E  is an exemplary block diagram of a front-end unit for FDD operation of an IBR. 
         FIG. 3F  is an alternative exemplary block diagram of an IBR antenna array. 
         FIG. 3G  is a block diagram of a front-end transmission unit according to one embodiment of the invention. 
         FIG. 3H  is a block diagram of a front-end reception unit according to one embodiment of the invention. 
         FIG. 3I  is a diagram of an alternative view of an exemplary horizontally arranged intelligent backhaul radio antenna array according to one embodiment of the invention. 
         FIG. 3J  is a diagram of an alternative view of an exemplary vertically arranged intelligent backhaul radio antenna array according to one embodiment of the invention. 
         FIG. 3K-A  is an illustration of the MIMO station propagation matrix elements. 
         FIG. 3K-B  illustrates the MIMO channel propagation matrix equation and associated terminology. 
         FIG. 3L  is an exemplary illustration of intelligent backhaul radios (IBRs) deployed for cellular base station backhaul with obstructed LOS. 
         FIG. 4A  is a table of a partial listing for the frequency availability for specific radio services 47 C.F.R. § 101.101, and a proposed new band of operation for Advanced Backhaul Services. 
         FIG. 4B  illustrates an exemplary deployment for occupancy of services in the 7125 to 8500 MHZ frequency band for legacy radios and Advanced Backhaul Services (ABS) compliant radios amongst other services. 
         FIG. 4C  illustrates an exemplary embodiment of Advanced Backhaul Service tiered service radio interconnection with an exemplary ABS device registry database. 
         FIG. 4D  illustrates an exemplary deployment of an embodiment of Advanced Backhaul Services tiered service radios within an exemplary geographic region. 
         FIG. 4E  illustrates exemplary embodiment of a deployment of intelligent backhaul radios (IBRs) is deployed for cellular base station backhaul with obstructed LOS in the presence of Tier 1 Incumbent radios according to an embodiment of ABS services. 
         FIG. 4F  illustrates an alternative exemplary embodiment of a deployment of intelligent backhaul radios (IBRs) deployed for cellular base station backhaul with obstructed LOS in the presence of Tier 1 Incumbent radios according to an embodiment of ABS services. 
         FIG. 4G  illustrates an exemplary deployment of an intelligent backhaul system (IBS) in the presence of an existing exemplary deployment of Tier 1 incumbent radios according to one embodiment of the invention. 
         FIG. 4H  illustrates a normalized antenna gain relative to an angle from bore utilizing an exemplary antenna system. 
         FIG. 5A  is an exemplary block diagram of an IBR including a Signature Link Processor (SLP). 
         FIG. 5B  is an exemplary block diagram of a Signature Link Processor (SLP). 
         FIG. 5C  is an exemplary block diagram of a signature control channel modem. 
         FIG. 5D  is an illustration of an exemplary Advanced Backhaul Services (ABS) compliant signal including an in-band and inline signature signal deployed within a single channel. 
         FIG. 5E  is an illustration of an exemplary Advanced Backhaul Services (ABS) compliant signal including an in-band and inline signature signal deployed within a multiple channels. 
         FIG. 5F  is an illustration of exemplary embodiments of Advanced Backhaul Services (ABS) signature signals of various structure. 
         FIG. 5G  is an illustration of an exemplary Advanced Backhaul Services (ABS) compliant signal including an in-band and embedded signature signal. 
         FIG. 5H  is an exemplary block diagram of an embodiment of a Sliding Correlator (SC). 
         FIG. 5I  is an exemplary block diagram of an embodiment of a Complex Sliding Correlator Block (CSCB). 
         FIG. 5J  is an exemplary block diagram of an embodiment of a Sliding Detector (SD). 
         FIG. 5K  is an exemplary block diagram of an embodiment of an inband inline signature detector. 
         FIG. 5L  is an exemplary block diagram of an embodiment of an inband embedded signature detector. 
         FIG. 6A  is an illustration an exemplary Advanced Backhaul Services layered control link communication protocol stack. 
         FIG. 6B  is an exemplary block diagram of an embodiment of an Advanced Backhaul Services control link protocol processor 
         FIG. 6C  is a flow diagram of the MAC receive process for an Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. 
         FIG. 6D  is a flow diagram of the MAC transmit process for an Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. 
         FIG. 6E  is an illustration of the radio link protocol (RLP) message format of Advanced Backhaul Services control link control link according to one embodiment of the invention. 
         FIG. 7A  is a flow diagram of the RRC transmit process for an Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. 
         FIG. 7B  is a flow diagram of the RRC scan process for an Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. 
         FIG. 7C  is a flow diagram of the RRC Bloom process for an Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. 
         FIG. 8A  is an illustration of exemplary ABS registry entries according to one embodiment of the invention. 
         FIG. 8B  is a flow diagram of the Common Control Channel basic broadcast alert process for an Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. 
         FIG. 8C  is a flow diagram of the Management Entity (ME) Tier 2 channel selection and link initialization process for an Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. 
         FIG. 8D  is a flow diagram of the Management Entity (ME) Tier 3 channel selection and link initialization process for an Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. 
     
    
    
     DETAILED DESCRIPTION 
       FIG. 4A  is a table of a partial listing for the frequency availability for specific radio services 47 C.F.R. § 101.101, and a proposed new band of operation for Advanced Backhaul Services ( 4 A- 01 ). The new band for Advanced Backhaul Services is not currently listed as a defined service within the table for fixed microwave services. Specific embodiments of the disclosed invention for an Advance Backhaul service (ABS) operate within a band from 7125 to 8500 MHz, and include a number of tiered services. Currently this band is not under the control of the FCC, but may have fixed point to point services defined for government operation by the Office of Spectrum Management (OSM) within the National Telecommunications &amp; Information Administration (http://www.ntia.doc.gov/office/OSM). The OSM manages the Federal government&#39;s use of the radio frequency spectrum, and may be thought of as filling a similar role for the federal government as the FCC does for the commercial sector. Currently, most of this band is defined as government exclusive operation as can be seen within the NTIA&#39;s “Redbook” defining spectrum allocations for use by the Federal government (http://www.ntia.doc.gov/files/ntia/publications/redbook/2013/4b_13.pdf). The frequency band ( 4 A- 01 ) is provided as an example only, and other bands of operated are contemplated for use with the embodiments disclosed. 
       FIG. 4B  illustrates an exemplary deployment for occupancy of services in the 7125 to 8500 MHZ frequency band for legacy radios and Advanced Backhaul Services (ABS) compliant radios amongst other services. The services deployed within this band according to embodiments of the invention, may be time division duplex (TDD), frequency division duplexed (FDD) or zero division duplexed (ZDD). FDD systems utilize separate frequency channels for receiving ( 4 B- 10 ) and transmitted signals ( 4 B- 50 ) to each radio, as shown in  FIG. 4B . TDD systems utilize a single frequency channel ( 4 B- 30 ) and alternate receiving and transmission with the radio to which they are communicating, allowing for the deployment of such services in the center of the operational band, as shown in  FIG. 4B . As previously discussed, ZDD systems utilize signal processing techniques to allow the simultaneous transmitting and receiving of signals on the same frequency channels. Generally ZDD systems could utilize similar channels to those of the TDD operating radios, but this is not a requirement and thus ZDD systems may be able to use any of the FDD or TDD channels. 
     The spectrum in the embodiment defined in  FIG. 4B  is partitioned into 3 Sub-Bands: 
     SB1=7126.5-7574.5 MHz (Channels 1 to 32) 
     SB2=7588.5-8036.5 MHz (Channels 34 to 65) 
     SB3=8050.5-8498.5 MHz (Channels 67-98) 
     Additionally Channels 33 ( 4 B- 20 ) and  66  ( 4 B- 40 ) are defined as Common Control Channels (CCC), to be used for advertising the presence of ABS devices, intercommunication between ABS devices with respect to interference coordination and other control and overhead functions in specific embodiments. 
     Channelization 
     In one embodiment, a network-based registry  4 C- 60 / 4 C- 70  (of  FIG. 4C ) will provide for a maximum number of channels out of the total number of channels available for operation for use by a particular device (or Tier as will be explained associated with  FIG. 4C ), either dependent, or independent of duplex mode of operation. 
     As will be discussed associated with subsequent figures, and specific embodiments, ABS services may include multiple groups of “Tiers” of devices, each tier having specific rules by which they must operate and result in interference protection between and among tiers of devices (such devices being referred to as tiered service radios). Such rules may also provide for a fairness to access of channels to prevent some devices from unfairly using more spectrum channels than would be fair to other devices, and preventing a reasonable number of devices within a geographic region to operate simultaneously. 
     For example, in one embodiment associated with  FIG. 4B , the individual channels of operation are 14 MHz in Bandwidth, as is common for fixed wireless in the United States (ranging from 3.5 MHz, 7 MHz, 14 MHz, etc). In other embodiments, such as for use is Europe, channels of 5 MHz, 10 MHz, or other multiples are more common. 
     Any given link must use and register up to 2 N     MAX    channels of 14 MHz each from amongst designated channels. FDD products typically register to transmit in 2 N     MAX     −1  channels of SB1 in one direction and to transmit in 2 N     MAX     −1  channels of SB3 in the opposite direction for a given link, however FDD products are not required to use this SB1/SB3 duplex approach. 
     The selection of the number of channels for operation, as mentioned for some embodiments, may be determined based upon the tier of service a device belongs to, and determined according to parameters provided by accessing a registry and may be specific to a geographic region. 
     In one example, for Tier 2 products, N MAX =3 (e.g. 2 N     MAX   =8) resulting in 8×14 MHz, or 112 MHz would be typical in most geographic regions. In a related example, For Tier 3 products, N MAX =2 (e.g. 2 N     MAX   =4) resulting in 4×14 MHz, or 56 MHz would be typical in most geographic regions. The total number of channels that can be used by both transmitters in aggregate for any given link is M TOT =2 N     MAX   . 
     In the current embodiment, the M TOT  channels can be occupied by either or both transmitters at any time for a given link, and may be dependent on the Tier of service, and geographic region. An example of a geographic region is shown in  FIG. 4D  by the boundary lines  4 D- 10 ,  4 D- 15 ,  4 D- 20 , and  4 D- 25 . 
     Continuing with the current exemplary embodiment, M ACTUAL  is the actual number of channels (up to M TOT ), in use at any time. Once a tiered service radio (or tiered device) is registered, (thus, becoming a registered radio) to transmit M REG  channels in any of SB1, SB2, or SB3, such a product can transmit subject to sharing rules herein, on 1 to M REG  channels contiguously as available. In the current embodiment, non-contiguous Tx channels at a single transmitter are not allowed. 
     According to the rules of the current embodiment, all transmitters (tiered service radios for example) are fixed and registered prior to first usage (including Tier 3 devices). In an exemplary embodiment, no devices are mobile. 
     In one embodiment, the registration may include Tx location, antenna parameters, Tx channels(s) (or channel numbers), Tx power (or max tx power), signature parameters (such as code sequences, demodulation parameters, structures, identifiable aspects of the signature radio signals, etc.), acceptable co-channel sharing signatures (or classes of signatures), Tx signaling method(s), signature approach (inline versus embedded), signature power in dB relative to nominal Tx power level, and/or maximum registered Tx power. More detail and specific examples of exemplary registry entries are discussed associated with  FIG. 8A  in more detail. 
       FIG. 4C  illustrates an exemplary embodiment of Advanced Backhaul Service tiered service radio interconnection with an exemplary ABS device registry database. In one embodiment, each tiered service radio (or tiered device) has specific rules and procedures, which are required to be followed, except for a legacy device. The tiered service radios provide for interference protection for legacy devices, or from other devices at the same or lower tier. Membership to a tier varies based upon the specific tier. For example in the embodiment of  FIGS. 4A and 4B , utilizing spectrum with fixed point to point devices operating under existing rules, such devices as currently in use for Federal point to point wireless communications would be deemed to be Tier 1 devices  4 C- 10 . Such currently deployed devices would be deemed “legacy” Tier 1  4 C- 10 , where new devices which also belong to existing government users, would be deemed “incumbent” Tier 1 devices  4 C- 20 , and may have specific requirements for the deployed equipment differing from the currently deployed legacy Tier 1 devices. In one embodiment Tier 1 devices  4 C- 10 ,  4 C- 20  would be protected from interference by requiring lower tier devices ( 4 C- 30 ,  4 C- 40 ) to perform a registry look up for a specific geographic region. Specific criteria, in some embodiments, is passed to the registry so as to retrieve information related to the registered radios on interest. In this embodiment, it would be a requirement of the devices, of lower tiers of service performing the registry look up, utilizing specific criteria, to be able to determine, or to be provided, their current geographic coordinates. In other embodiments, the specific criteria may be a subset or inquiry criteria and be within the tiered service radio and used to filter the information returned from the registry. In further embodiments, specific criteria such as geographic location, tier of the inquiring device, etc., may be passed to the registry as inquiry criteria and the filtering and/or selection of information performed within the registry completely. In yet further embodiments, the selection of information from the registry based upon the specific criteria may be performed on one or both of either the inquiring tiered service radio or the registry apart (or in combination). 
     Returning to the current description, the only protection a legacy Tier 1 device  4 C- 10  would have is the registry  4 C- 70  with a pre-defined exclusion zone associated with a geographic location. Such an exclusion zone within may be defined by one or more center points, and a radius from each center point, or another definable geographic shape such as a rectangle, or an ellipse, or the like. An example of such an exclusion zone is provided in  FIG. 4D , associated with exclusion zone  4 D- 35 . Exclusion zone  4 D- 35  provides for an ellipse as defined within the server  4 C- 60  and registry database  4 C- 70 . Lower tier devices, such as Tier 2 Devices  4 C- 30  and Tier 3 Devices  4 C- 40 , connect to server  4 C- 60  and registry database  4 C- 70  via network connections  4 C- 35 ,  4 C- 45 , and  4 C- 65 , and over an interim network  4 C- 50  in some embodiments. Such a network  4 C- 50  may be a private network, or the public Internet, or both. Additionally, Incumbent Tier 1 devices may include a network connection  4 C- 25  in some embodiments. Incumbent Tier 1 Devices  4 C- 20  may additionally become a registered radio with the registry database  4 C- 70  in some embodiments, or may transmit an alert message advertising the Incumbent Tier 1 Device&#39;s presence, or perform both registration as well as advertisement. Such an advertisement may be performed in a number of ways including on the so-called common control channels ( 4 B- 20 ,  4 B- 40 ) and associated with  FIG. 4B . In other embodiments, alerts may be transmitted inband so as to allow for an accurate assessment of the received signal from the Tier 1 device, and to determine an acceptable transmission power so as to ensure no detrimental interference to the Tier 1 Device. An example of Incumbent Tier 1 devices operating utilizing in-band alert transmission is provided associated with  FIG. 4D . Incumbent T1 Device (T1-I)  4 D- 40 -A is in communication with T1-I  4 D- 40 -B, both transmitting an alert signal, including information identifying the device and either including the transmitted power within the alert, or retrievable from the registry database. Additional information may be included with the transmission or within the registry as well such as locations of the devices, and frequencies or operation, and mode (TDD/FDD/ZDD) of the device, and the like. More detail related to embodiments of the registry entries are provided associated with  FIG. 8A . For example, such information can be used to determine the propagation path loss to the transmitter or to estimate path loss to potential receivers associated with the stations. Tier 2 devices  4 D- 60 -A,  4 D- 60 -B may utilize transmission limits as determined from such parameters so as to operate in closer proximity to the T1-I devices  4 D- 40 -A and B, rather than simply utilizing an exclusion zone. 
     Referring back to  FIG. 4C , Tier 2 Devices are registered users (or registered radios) and are provided with a license, which offers interference protection relative to other Tier 2 devices, and Tier 3 devices. Tier 2 devices (T2), in some embodiments, have no interference protection from Tier 1 devices (Legacy or Incumbent). To receive a license, operators of T2 devices may pay a fee that may be determined by in a number of ways, in various embodiments. Such a fee may be based upon:
         i. number of channels up to a maximum for initial registration, and annual usage per link for a specific geographic region, and/or   ii. by Auction, and/or   iii. by Status (such as, for example only, providing a service deemed a public good)       

     Exemplary rules that may be required for Tier 2 devices include:
         Tier 2 users must not use, or must vacate upon detection, channels occupied by Tier 1 users.   Tier 2 users must occasionally re-check the registry database (based upon time, duration, or the like).   Tier 2 devices must advertise their presence by transmitting an Alert signal including a T2 Alert Signature, and registering within the registry data base  4 C- 70  (or becoming a registered radio), including the start time of their active operation and other details, such as for example, described associated with  FIG. 8A .       

     An example of a T2 device being prevented from operating, as according to the foregoing rules, is provided associated with  FIG. 4D , and T2 device  4 D- 45 . The T2 device  4 D- 45  is geographically too close to T1-I device  4 D- 40 -A, and upon performing a scan of the radio environment detects alerts from the T1 device (for example a signature radio signal in one embodiment), and thus T2 device  4 D- 45  is prevented from operating on the same channel(s) on which T1-I device  4 D- 40 -A operates. If other unoccupied channels are available, the T2 device  4 D- 45  would be not be prevented from attempting operation on those alternative channels, unless those channels were otherwise not allowed due to yet another device&#39;s exclusion zones, or alert signature transmissions that could be detected. 
     An example of rules for an embodiment for T2 devices to achieve interference protection from other T2 users is:
         Tier 2 users must not use channels already occupied by other Tier 2 users as either:
           i. Detectable at a threshold with a valid Tier 2 signature, or   ii. Registered (as a registered radio) in a look up for a geographic location within a Tier 2&#39;s exclusion zone, unless   iii. Existing channel occupant Tier 2 user with “precedence” agrees to accept the presence of the new channel occupant tier 2 user. For these purposes precedence is defined as the device having initiated continuous operation on a channel (s) earlier in time, as entered within the registry.   
               

     Just as Tier 1 devices, in the current embodiment, have priority and are protected from interference from Tier 2 devices, Tier 2 devices have priority and are protected from interference from Tier 3 devices  4 C- 40 , of  FIG. 4C . In this embodiment, priority indicates that a device may be placed in the presence and cause interference to another device of lower priority, thus causing the lower priority device (or lower Tier device) to modify operating parameters (or adjustable network parameters) such as channel of operation, transmission power, antenna selection, transmit or receive antenna beam patterns, polarization, or the like. Further upon alert detection, registry entry read, or direct notification to the lower Tier device by a higher Tier device, that a tiered service radio is present, the lower tier device as a lower priority tiered service radio must cease operating (in one embodiment) and re-initialize operating according the rules associated with that Tier&#39;s operation. In specific embodiments, Tier 2 devices, being licensed and registered (as registered radios), have priority over Tier 3 devices (T3), and receive interference protection from the Tier 3 devices. According to one embodiment, Tier 3 devices must be certified to obey operating rules of their Tier, but would not be licensed to a channel or geographic region and may not be required to pay any type of a fee associated with a license. Example rules for operating Tier 3 devices are as follows, according to one embodiment: 
     Tier 3—Unlicensed users
         Allowed to use up to “unlicensed max” number of channels for a specific geographic region as determined by registry look up, and   Wherein Tier 3 users must not use, or must vacate upon detection of any Tier 1 or Tier 2 user at any time   Wherein Tier 3 users must certify:
           i. Detection capability for Tier 1 and Tier 2 signatures, and   ii. The ability to access the registry prior to transmitting on the ABS channels   
               

     The various tiers of devices have interference priorities and obey sharing rules. However, specific embodiments may provide for certain channels to be reserved for specific tiers of operation to ensure fair access to the spectrum resources. For example, in one embodiment associated with  FIG. 4B , Channels 1, 2, 34, 65, 97, 98 plus other channels as designated for any given geographic zone within the registry are Tier 2 Exclusion Channels. Tier 2 products can use such channels but receive no protection from Tier 3 transmitters. This ensures that Tier 3 devices can never be completely precluded from all operation in any given geographic region by a high density of Tier 2 devices. 
     As described above, in embodiments of ABS services, T1-Incumbent, T2, and T3 devices are required to transmit an alert having a signature sequence. In other embodiments, only T3 devices, or both T3 and T2 devices are required to transmit an alert signature. The alert signature may vary in different embodiments of the invention, and may be transmitted on the common control channels in some cases, or within the band of operation (in-band) in other embodiments. Further, when the alerts are transmitted in-band they may be “in-line” or “embedded”. One example of an embedded signature sequence was disclosed associated with co-pending application U.S. Ser. No. 13/763,530, the entirety of which is incorporated herein by reference. The structure of the alert signals and the signatures within them are described in further detail with respect to  FIG. 5D ,  FIG. 5E ,  FIG. 5F , and  FIG. 5G . 
     In one embodiment, all transmitters required to transmit an alert must transmit signatures having at least 0.01% (or −40 dBc) of the nominal transmit energy in every 1 s period (P NOM ×1 s) based upon relative transmit time and relative transmit power. 
     In one exemplary embodiment, a signature of duration 100 μs can be transmitted either in-band/in-line, in-band/embedded, or on the common control channel. Further embodiments may include transmitting an alert signature from a receiver antenna, so as to enhance the potential for determining interference potential and accuracy or to aid the estimation of the interference potential from other ABS devices. Such an approach may be applicable for ZDD and/or TDD based devices, or FDD devices any of which may utilize interference cancelation approaches at the receiver to remove the transmitted alert. Alternatively such an approach may utilize in-line bursts of the alert signal in designated non-reception time periods at the receive antenna. 
     In one example of inline signaling for an in-band/inline alert, a burst signature at P NOM transmission power level for 100 μs is utilized, one every second. In another example, an alert signature may be transmitted multiple times per second, but at a power level of 
     
       
         
           
             
               P 
               NOM 
             
             
               
                 T 
                 SIG 
               
               
                 100 
                 ⁢ 
                 
                     
                 
                 ⁢ 
                 us 
               
             
           
         
       
     
     so as to result in the same integrated power over the 1-second period. As a result, a receiving device can be sure of the integrated receive power per unit time, relative to the nominal transmission power of the signal carrying information. Such a process of interference estimation further enhances the ability of the detecting device to assess the potential for interfering with the detected device upon beginning transmissions from the detecting device. 
     In another embodiment where the alert is transmitted on the Common Control Channel ( 4 B- 20  and/or  4 B- 40 ) one alert will be transmitted at a random time within every 1 ms time period, including a 100 μs burst signature at P NOM , again allowing for the estimation of the power level of the detected alert relative to the information signal from that transmitting device. 
     The common control channel is further available for non-protection signaling broadcasts instead of inline signatures. For example, the common control channel may be utilized for intercommunication between tiered service radios, in contrast to simply advertising the presence of the device so as to make tiered service radios of a relative lower tier refrain from interfering with the instant tiered service radio (e.g. protection signaling). 
     One embodiment of the common control channel is available for limited frame exchanges for any Tier 2 or 3 transmitters without current registration subject to such exemplary restrictions as:
         P LIMIT =P NOM , and modulation is only within channel   Max 100 us frame duration that is randomly chosen   Max 1 frame per TX Period of 1 ms   Max 100 frames per TX per second   At least one signature frame per Tx per second       

     One embodiment of a signature and associated payload will now be discussed, which includes a unique 32 bit address assigned as a 16 bit manufacturer code and a 16 bit random address. The alert may also include the transmission or reception channels, and may be modulated utilizing non-coherent DQPSK or DBPSK using a code sequence. In various embodiments, the code sequence is a direct sequence spreading code, and utilize one or more of a Barker, PN, maximal length code, CAZAC, Gold, Zadoff-Chu, and the like. 
     In one example having 1 signature of length 100 us in a 14 MHz channel results in ≈12.39 Msym/s or 1238+ symbols/100 us when using a root raised cosign filter of 1.13. The information bits may further utilize a ½ rate Reed Muller or Reed Solomon Code (for Parity Check), and be modulated according to DQPSK. One embodiment would then result in at least 37 spreading “chips” per bit, with 32 bits of information. 
     Alternative embodiments of the structure and processing of alerts and their transmission and associated layered protocols will be provided associated with subsequent figures. 
     Transmission Power of ABS Signals 
     Associated with the example embodiment of  FIG. 4B , and having 14 MHz channels, the power limit for a given device may be given by: 
     
       
         
           
             
               P 
               LIMIT 
             
             = 
             
               
                 P 
                 NOM 
               
               + 
               
                 10 
                 * 
                 
                   log 
                   ⁡ 
                   
                     [ 
                     
                       
                         Aggregate 
                         ⁢ 
                         
                             
                         
                         ⁢ 
                         Information 
                         ⁢ 
                         
                             
                         
                         ⁢ 
                         Rate 
                       
                       
                         28 
                         * 
                         
                           M 
                           ACTUAL 
                         
                       
                     
                     ] 
                   
                 
               
             
           
         
       
     
     Where P NOM  is the nominal power level determined from the registry for the given tier of service, and the geographic operating region. 
     Further the maximum equivalent (or effective) isotropically radiated power for a given tiered service radio is determined by 
       Max EIRP= P   LIMIT   *G   TxMAX    
     where G TxMAX  is max Tx antenna gain limit for a given geographic zone. 
     Each ABS device must further demonstrate and be certified to perform transmit power control over P NOM −10 dB to P MAX  (where P MAX ≤P LIMIT ). 
     As previously described, the alerts may be utilized so as to determine the potential for interfering with other devices within the area such that antenna and transmission parameters (as adjustable network parameters) may be adjusted so as to reduce the potential for interfering with higher tier devices, or devices of the same tier but with a earlier occupancy of the channel (precedence). As will be discussed further, upon the detection of an alert from a device of the same or lower tier, but with lower precedence if from the same tier, procedures are disclosed by which the two devices may cooperatively reduce the interference levels to acceptable levels, or by which the lower tier or lower precedent device may be forced to discontinue transmission all together. Such cooperative interference mitigation approach will be discussed associated with subsequent figures, in particular  FIG. 8C  and  FIG. 8D . 
     Turning now to  FIG. 4E , an exemplary embodiment of a deployment of intelligent backhaul radios (IBRs) is deployed for cellular base station backhaul with obstructed LOS in the presence of Tier 1 radios according to an embodiment of ABS services. 
       FIG. 4E  illustrates a deployment scenario according to one embodiment of the invention. In this example, Incumbent Tier 1 device (T1-I)  132   a  utilizes an unobstructed line of sight wireless link  136  to T1-I  132   b . The T1-Is have a relatively narrow beam (e.g., 3 dB width of 2 Degrees in both azimuth and elevation). A tall building  312  is located between T1-I  132   a  and T1-I  132   b . The building  312  is short enough that it does not adversely impact link  136  because each T1-I has a relatively narrow beam. 
       FIG. 4H  illustrates a T1-I antenna pattern having a similar main antenna beam width and other antenna pattern attributes as the T1-Is  132   a ,  132   b  of  FIG. 4E . It is relevant to note that while the T1-I antenna pattern depicted in  FIG. 4H  possesses a narrow 3 dB main beam width  4 H- 40  relative to the peak gain  4 H- 10  in the antenna bore sight direction, there remains the possibility for signal reception from angles beyond the 3 dB beam width points, but with lesser relative antenna gain levels. For example, the gain level at twice the 3 dB beam width may be as significant as −10 dB or −15 dB relative to the main bore sight gain  4 H- 10 . Furthermore, the gain at side lobe  4 H- 20  remains within −20 dB, in this example, relative to the peak bore sight gain  4 H- 10 , and is located at roughly 3 times the angular separation from the bore sight direction as the 3 dB main beam radius. In contrast, antenna nulls, including nulls  4 H- 30 , are points where the residual gain from the T1-I antenna is at a significant minimum level and are generally interspersed between side lobes or other higher gain portions of the antenna pattern. The antenna pattern depicted in  FIG. 4H  represents a typical T1-I antenna pattern, such as one produced by so called parabolic dishes including, generally, a circularly symmetric antenna gain pattern about the bore sight. 
     As discussed in additional detail in this disclosure and the co-pending applications previously incorporated by reference, the use of multi-element antenna systems, in some configurations, allows an antenna array&#39;s beams, side lobes, and nulls to be advantageously directed. By the advantageous angular placement of an antenna array&#39;s main gain lobe, and the placement of lower gain portions of the antenna array&#39;s gain pattern in specific other directions, a desired link may be maintained while managing the level of undesired signal transmitted to or received from other transceiving radios (including T1-Is) in the area. The antenna arrays may utilize adaptive techniques incorporating transmission null steering or reception null steering approaches. In one embodiment, adaptive antenna array processing, including null steering algorithms, are utilized to allow for the deployment of RE-IBR  4 E- 20  and AE-IBR  4 E- 10  of  FIG. 4E  (as either T2 or T3 devices) in the presence of T1-Is  132   a  and  132   b  so as to not impact the T1-Is  132   a,b  receiver performance by reducing interfering signal levels from each IBR impinging upon the T1-I antenna gain patterns. As estimate of the relative interference from the T2 or T3 devices to the T1-I devices may be determined utilizing the detection of the alert signature transmitted from the T1-I devices. 
     In one embodiment, the antenna elements  352 A of  FIGS. 3A to 3H  (e.g., utilized by IBR  4 E- 10  and  4 E- 20 ) have a 3 dB antenna beam width in elevation of 15 degrees and a 3 dB antenna beam width of 30 degrees in azimuth. Such individual antenna pattern radiation patterns may cause interference to deployed T1-Is in the geographic area. In one example, the signal transmissions from RE-IBR  4 E- 20  to T1-I  132   a  via propagation path  4 E- 60  are received at a sufficient level so as to cause a degradation of the T1-I link  136  performance. In another example, a signal transmitted from AE-IBR  4 E- 10  along a signal propagation path  4 E- 70  is scattered from building  312  and received in a side lobe of the antenna pattern of T1-I  132   b  at a sufficient level to also impact the T1-I to T1-I link performance. 
     In one embodiment, the RE-IBR  4 E- 20  and AE-IBR  4 E- 10  utilize a multi-element antenna array such as depicted in  FIG. 3I . Such an antenna array configuration allow for spatial array processing. Such spatial array processing may include phased array processing, digital beam forming, transmission null steering, elevation and azimuth beam steering, antenna selection, beam selection, polarization adjustments, MIMO processing techniques, and other antenna pattern modification and spatial processing approaches for both the transmission and reception of signals. It will be appreciated that other antenna array configurations may be used, which have more or fewer antenna elements than the exemplary IBR antenna arrays depicted in  FIGS. 3I and 3J , and which have different geometrical arrangements, polarizations, directional alignments and the like. 
     Embodiments of the invention are advantageous because the impact to the T1-I link performance can be reduced or eliminated completely while allowing for the deployment of the IBR  4 E- 10  and IBR  4 E- 20  in the same geographical region as the T1-I devices  132   a  and  132   b  with sufficient inter-IBR link  4 E- 50  performance. In some embodiments, IBR deployments may be enabled in the same geographical areas and within the same frequency bands, and in further embodiments such deployments may be in a co-channel configuration amongst a T1-I link and an IBR link, while allowing for sufficient performance between IBR  4 E- 10  and IBR  4 E- 20 . 
     With reference to  FIGS. 4F and 4G , specific embodiments of Tier 2 or Tier 3 devices are described with respect to reducing interference to co-channel Tier 1 devices according to an embodiment of the ABS services. 
       FIGS. 4F and 4G  illustrate additional exemplary deployments of IBRs in the presence of T1-Is.  FIG. 4F  is a side perspective view of elements of a deployment embodiment example, and  FIG. 4G  is a top perspective view of the deployment embodiment. It should also be noted that some geometrical differences exist between  FIG. 4F  and  FIG. 4G  to provide illustrative descriptions. Where  FIG. 4F  and  FIG. 4G  are in conflict or otherwise are inconsistent, the differences should be considered alternative embodiments. 
     Intelligent backhaul radios RE-IBR  4 F- 20  and AE-IBR  4 F- 25  are deployed with configurations as previously discussed in the related embodiments of IBRs  4 E- 10  and  4 E- 20 . The IBRs  4 F- 20  and  4 F- 25  are deployed for cellular base station backhaul with obstructed LOS propagation link  4 F- 60  according to one embodiment of the invention. 
     In  FIGS. 4F and 4G , T1-I A  4 F- 05  and T1-I B  4 F- 10  are deployed for cellular base station backhaul with unobstructed line of sight (LOS) propagation link  4 F- 15 . T1-Is  4 F- 05  and  4 F- 10  are deployed within the same geographical region of the IBRs  4 F- 20  and  4 F- 25 . Each of T1-I  4 F- 05  and  4 F- 10  uses an antenna pattern, with 3 dB main beam width. Additional properties of T1-Is  4 F- 05  and  4 F- 10  are, in one embodiment, the same as those described with respect to T1-Is  4 G- 05  and  4 G- 10  of  FIG. 4G . 
     In the embodiment shown in  FIG. 4F , antenna elements  352 A (see, for example,  FIGS. 3A-H ) are utilized by IBR  4 F- 20  and  4 F- 25  and have a 3 dB antenna beam width in elevation of 15 degrees and a 3 dB antenna beam width of 30 degrees in azimuth. Such individual antenna pattern radiation patterns may cause interference to deployed T1-Is in the geographic area. In one example, the signal transmissions from RE-IBR  4 F- 20  to T1-I  4 F- 05  via propagation path  4 F- 30  are received at a sufficient level to cause a degradation of performance of the T1-I link  4 F- 15 . In another example, a signal transmitted from AE-IBR  4 E- 25  along signal propagation path  4 F- 40  and  4 F- 45  is scattered and attenuated from building  4 F- 50  but has a sufficiently low level so as to not cause performance degradation to intended signal reception at either of T1-I  4 F- 10  or IBR  4 F- 25 . 
     As explained above, in  FIG. 4F , RE-IBR  4 F- 20  and AE-IBR  4 F- 25  are deployed for cellular base station backhaul with obstructed LOS propagation link  4 F- 60 . Additionally, with respect to the present embodiments of  FIGS. 4F and 4G , RE-IBR  4 F- 20  and AE-IBR  4 F- 25  utilize a multi-element antenna array, such as antenna array  348 A of  FIG. 3A or 3B . The antenna array  348 A allows for various spatial array processing. As described above, such spatial array processing may include phased array processing, digital beam forming, transmission null steering, elevation and azimuth beam steering, antenna selection, beam selection, polarization adjustments, MIMO processing techniques, and other antenna pattern modification and spatial processing approaches for both the transmission and reception of signals. It should be noted the current embodiment is only one configuration, and that other embodiments may utilize more or fewer antenna elements and with varying geometrical arrangements, polarizations, directional alignments and the like. 
     Embodiments of the invention relate to determination of IBR network parameters (including adjustable network parameters) and the installation and commissioning process of remote end IBRs (RE-IBRs) and Aggregation End IBRs (AE-IBRs). A detailed process for installing and commissioning the IBRs (or tiered service radios in general) is described in further detail below. These processes and/or some of the process steps may be may be performed using one more of IBRs and IBCs (or Intelligent Backhaul Controller) of  FIG. 4G , or elements of an Intelligent Backhaul Management System (or IBMS  420  in  FIG. 4G ) including IBMS Private Server  424 , IBMS Private Database  432 , IBMS Global Server  428 , IBMS Global Database  436 , the Private Database  440 , and the processing and storage elements accessible utilizing the public internet such as the Cloud computing resource  456 , Public Database  452 , and Proprietary Database. Additional details describing the IBC and IBMS and exemplary relationships to IBRs are found in co-pending application U.S. Ser. No. 13/271,051 for the Intelligent Backhaul System (or IBS), the entirety of which is incorporated by reference herein. 
     During installation or during deployment and operation of the IBRs  4 F- 20 ,  4 F- 25 , the IBS, IBMS and other public and private network elements such as the registry server  4 C- 60  and database  4 C- 70  (which may collectively include a registry in some embodiments) may use information stored with one or more network elements to determine or aid in the determination of IBR operational parameters (adjustable network parameters for example) for allowing co-band or co-channel operation with manageable interference impact to and from T1-Is  4 F- 05  and  4 F- 10  or other aforementioned services within a geographic zone, or within a known radio frequency propagation distance. 
     Exemplary IBR operational parameters (adjustable network parameters) include but are not limited to: the selection operational frequencies; the modification of transmitter antenna patterns; the modifying or selection of antenna polarization or spatial patterns; the selection of specific antennas from a set of available antennas; the selection of transmission nulls, reducing the interference impinging upon other systems; the selection of receiving or transmission digital beam forming weights, or algorithmic beam forming constraints; the physical movement, placement, alignment, or augmentation of one or more antenna elements or antenna arrays by electrical, or electromechanical control or by a request for manual adjustment or augmentation during or after installation; the modification of transmission power; and the selection of interference margin values for the reduction of the risk in interfering existing systems. 
     In one embodiment, the determination of the IBR operational parameters (adjustable network parameters) is performed utilizing an algorithm based at least in part on the location of the T1-Is  4 F- 05  and  4 F- 10  and their radiation parameters. This information may be stored in the Universal Licensing System (ULS) operated by the Federal Communications Commission (FCC), or on other public or private databases or the registry server as shown in  FIG. 4C  ( 4 C- 60 / 4 C- 70 ). In one embodiment, ULS information and associated radiation parameters in combination with radio frequency propagation models are utilized to determine the level to which operation of an IBR, under various IBR operational parameters would interfere with one or more Tier 1 Incumbent or Legacy services. In another embodiment, reports of received signal are provided by IBRs, possibly in combination with existing IBR operational parameters, to the IBMS for use in IBR operational parameter determination. Such reports may be stored by the IBMS and used alone or in combination with T1-I or T1-L radiation parameter information from public or private databases to perform IBR operational parameter selection. 
     Further embodiments may include an iterative method. For example, the IBRs may report received spectral measurements and configuration parameters to the IBMS, which performs selection of some or all for the operation parameters, and passing the parameters to respective IBRs. The IBRs may then perform additional or refined scanning upon initial operation prior to the determination of subsequent IBR operational parameters. 
     Upon initiating the configuration process in this embodiment, the respective IBRs perform a scan of receive channels to detect existing T1-Is. The scan process, in some embodiments, produces scan data. The IBRs then report their respective antenna configurations and scan results (scan data) to the IBMS. Note that in other embodiments, a centralized server may not be used at all, allowing for a distributed decision process based upon rules. Returning to the current embodiment, the IBMS, will determine, assuming another channel may not be used, the level of interference the T1-I will receive. In some embodiments, this determination is based also upon received signatures levels (signature radio signal levels for example) or alert level per the disclosed invention. The interference may be determined utilizing IBR effective antenna pattern adjustments and, optionally, associated information retrieved from a database of T1-I parameters. In some embodiments, the effective antenna pattern adjustments may include the use of transmission beam nulling from the required one or more IBRs to further reduce the interference levels which may be received at the T1-I, while maintaining a minimum required performance between the respective IBRs. In one embodiment, an interference margin is also calculated. The interference margin is used as an additional reduction of the required interference to the target T1-I. The interference margin may be based on a fixed amount; a level of uncertainty of the predicted interference, an amount based upon the reliability or predicted accuracy of interference calculations, or based upon using or the availability of, the specific values of T1-I antenna and operating transmission parameters retrieved from a database. 
     In some embodiments, the RE-IBRs and AE-IBRs may operate on channels for which no interference is detected, but are within a predetermined distance of T1-Is. The distance is determined based on the geographic location of the IBRs and the T1-Is. The location of the T1-Is may be determined by accessing, for example, the FCC (ULS) database. In such situations, the IBMS may utilize an interference margin value or other operational constraint value based upon propagation models to further reduce the likelihood of interfering with the T1-I. 
     In some embodiments, co-existence of the IBRs with FDD T1-Is may be required. In these embodiments, interference margins or operational transmission constraints, including transmission beam nulling, may need to be calculated. For example, in one embodiment, the selection of the transmission antennas to utilize for receive during a scan procedure during configuration may allow for enhancement of transmit beam forming and transmit nulling operations and may further aid in the determination of values related to transmission beam nulling. 
     In some embodiments, received signals transmitted from a T1-I  4 F- 05  operating in FDD are detected during a scan procedure at an IBR  4 F- 20 . However, the IBR to IBR link, in one deployment, is configured to operate on the specific FDD paired frequency co-channel used for receiving by the FDD T1-I  4 F- 05  as determined, for example, by the IBMS  420  in  FIG. 4G  and FCC data base records in a public data base  452 , or the registry server  4 C- 60  and database  4 C- 70 . In this embodiment, transmission beam nulling weighs for the T1-I  4 F- 05  receiving channel (uplink paired channel used by T1-I  4 F- 05  for receiving from T1-I  4 F- 10 ) or other transmission constraints may be determined based upon the received signals at the IBR  4 F- 20  in the paired (downlink paired channel as used by T1-I  4 F- 05  to transmit to T1-I  4 F- 10 ) channel, despite the frequency difference for the transmission channel. Such calculations may utilize propagation modeling to determine interference levels, reported measurements by the IBR to determine the level of frequency flat or frequency selective fading, and data base values related to T1-I parameters. In this embodiment, these calculations involve a constrained transmission beam forming calculation for example, including an interference margin based at least in part upon the determined level of flat or selective fading of the scanned signal on the paired band. 
     Embodiments of the invention allow for IBR adjustable network parameters to be selected to avoid co-channel operation with T1-Is. In deployments where co-channel operation between the IBRs and T1-Is is not avoidable, the impact on link performance to the T1-I  4 F- 10  and from T1-I  4 F- 05  can be reduced or eliminated completely while allowing for the deployment of the IBR  4 F- 20  and IBR  4 F- 25  in the same geographical region with sufficient inter-IBR link  4 F- 60  performance. In some embodiments, the IBRs may be deployed in the same geographical areas and within the same frequency bands as T1-Is. In some embodiments, the IBRs and T1-Is may be deployed in a co-channel configuration, while still allowing for sufficient performance between IBR  4 F- 20  and IBR  4 F- 25 . 
     Referring now to  FIG. 5A , an embodiment of an IBR including a Signature Link Processor (SLP) is depicted. A number of the blocks common with  FIGS. 3A and 3B  are shown, whose functioning is generally described associated with the foregoing description. Relative to  FIG. 3B ,  FIG. 5A  provides for a modified IBR MAC  512 A, and an additional block referred to as a Signature Link Processor (SLP)  500 . 
     Embodiments of IBR MAC  512 A generally incorporate the functionality of the various embodiments of IBR MAC  312 A. Some Embodiments of IBR MAC  512 A may additionally include MAC processing supporting the optimization of the wireless links utilizing ECHO devices as described more fully in co-pending application U.S. Ser. No. 13/763,530, the entirety of which is incorporated herein by reference. Additionally some embodiments of IBR MAC  512 A will support peer to peer and communications with other devices (e.g. ECHO devices) utilizing a Signature control channel for the transfer of control information. 
     Embodiments of the Signature Link Processor (SLP)  500  provide for the reception and insertion of an additional wireless communications channel referred to as a Signature control channel in specific embodiments. Associated with IBR transmission, the Signature Link Processor receives transmit symbol streams (1 . . . K) from IBR Modem  324 A and provides the same transmit symbol streams (1 . . . K) to the IBR Channel MUX  328 A with additional Signature control channels added to the individual streams, if such processing is enabled. In some embodiments where Signature control channels are not actively associated with any specific transmit symbol stream, the transmit symbol streams are passed to their respective with no addition of Signature control channel signal. Embodiments of the SLP may provide for a unique Signature control channel to be added to each of the respective transmit symbol streams. In other embodiments the SLP may provide for the components of the control channel or the control channel in entirety to be added commonly to all transmit symbol stream in a related fashion. 
     In one exemplary embodiment utilizing a common control channel structure, a direct sequence spread spectrum (DSSS) pilot signal utilizing a first orthogonal code will be added commonly to all streams processed for transmission by the SLP. Additionally, in the instant embodiment, each individual stream will receive a respective second copy of the DSSS pilot signal, but modulated with a differing orthogonal code respectively associated with the individual transmit symbol streams. Such modulation may be accomplished using modulo 2 additions, multipliers, or bi-phase modulators as known in the art. The individual orthogonal codes may additionally be modulated by information bits in the form of the IBR_SLP_Data transmit data interface stream, resulting in a Signature control sub-channel symbol stream. One such reference teaching DSSS and CDMA modulation and demodulation techniques is  CDMA: Principles of Spread Spectrum Communications , by Andrew J. Viterbi (Addison Wesley Longman, Inc., ISBN: 0-201-63374-1). Some embodiments of the Signature control channel having a specific structure utilizing multiple sub-channels are referred to as a common control channel. The use of either term in specific instances should not be considered limiting, and in some cases is utilized interchangeably. 
     Embodiments of the Signature Link Processor (SLP)  500  further provide for the reception and demodulation of Signature control channels inserted into one or more transmitted symbol streams by other devices, such as an ECHO device. Associated with IBR reception, the Signature Link Processor  500  receives receive symbol streams (1 . . . L) from IBR Channel MUX  328 A and provides the same transmit symbol streams (1 . . . L) to the IBR Modem  324 A, with the detection and or demodulation of any associated Signature control channels within the individual streams, if such processing is enabled. The resulting demodulated data from the Signature control channels is provided to the IBR MAC  512 A by the SLP  500  as IBR_SLP_Data. Embodiments of the SLP may provide for a unique Signature control channel to be received and demodulated associated with each of the respective receive symbol streams. In other embodiments the SLP may provide for the components of the control channel or the control channel in entirety be detected and demodulated commonly from all receive symbol streams. 
     In alternative embodiments, with appropriate interfaces, the SLP may be placed between the IBR Channel Mux  328 A and the IBR RF  332 A so as to allow for a single Signature control channel on a per transmit or receive chain basis rather than on per symbol stream basis. 
     In yet further alternative embodiments, a similar per chain Signature control channel result may be obtained utilizing the SLP placement as shown in  FIG. 5A  but with amplitude and phase weightings so as to cause the IBR Channel MUX to achieve the intended result. Such combinations of IBR Channel MUX processing with coordinated SLP processing further allows for additional control of capabilities of mapping specific Signature control streams with specific transmit or receive chains associated with the IBR RF  332 A. 
       FIG. 5B  is an exemplary block diagram of an embodiment of the Signature Link Processor (SLP)  500 . The SLP controller provides for interfacing the SLP_Data, RRC and/or RLC with the Signature Control Channel Modem (or SCCM) data and control information denoted as SCCM_Data-(1 . . . KL) and SCCM_Ctrl-(1 . . . KL) via communication with the individual Signature Control Channel Modems ( 510 B- 1  . . .  510 B-KL). Such interfaces allow for the interchange of data, including and control information with the individual modems. For example the relative signal level and timing of the individual per stream Signature control channels and sub-channels within transmit symbol streams may be set utilizing the control information contained within the SCCM_Ctrl-kl signals (where kl varies linearly from 1 to KL). Additionally the correlated signal level of a Signature control channel or sub-channel, the received signal level indication of all the signals, and the timing information of the received signals may be additionally communicated from the individual SCCM Modems to the SLP Controller  520 B, and to the RLC, SLP_Data, and RRC subsequently. It should be understood that the SLP_Data signal of  FIG. 5B  corresponds to the IBR_SLP_Data signal of  FIG. 5A . However, as the SLP will be disclosed as being utilized in subsequent embodiments associated with ECHO devices, the naming within  FIG. 5B  is more generic. 
     Additionally, the DRx-kl signals (where kl varies from 1 to KL) provide for digitally sampled signals associated with the 1 to L receive symbol streams, in some embodiments. The DRx Out-kl signals (where kl varies from 1 to KL) are respectively coupled to DRx-kl, to provide for a pass through operation of the respective DRx-kl signals, for example when an SLP is utilized within an IBR. Such a pass through coupling, in some embodiments, allows for the coupling of the receive symbol streams from the IBR Channel MUX  238 A to the IBR Modem  324 A. In some alternative embodiments where the SLP is utilized within a repeater device, such DRx Out-kl signals may not be utilized by the repeater device and may not be depicted as external ports to the SLP in such embodiments. 
     The DTx_In-kl and DTx_Out-kl signals (where kl varies from 1 to KL) provide for a digitally sampled signals associated with the 1 to K transmit symbol streams respectively input and output from SLP  500 , in some embodiments. An individual Signature Control Channel Modem  510 B-kl, provides a modulated control channel (MTx-kl) to a respective exemplary Adder  514 B-kl, which combines MTx-kl with the input transmit symbol stream DTx_In-kl. Adder  514 B-kl in turn provides the Signature Control Channel Signal DTx_Out-kl. In embodiments where no input to a particular DTx_In-kl is provided, the MTx-kl signal is provided directly as DTx_Out-kl. 
     Note that KL need not be equal to either K or L. In some embodiments where there is a one to one correspondence between transmit symbol streams and Signature control channels (or sub-channels in a common control channel structure), KL must be equal to or greater than K. In cases where KL (the number of SCCMs) exceeds K (the number of transmit symbol streams) the excess SCCMs may not be utilized for transmission, or may be used for other purposes. One such purpose would be for use dedicated to a transmit chain, such as might be used with a single high gain antenna panel for example. 
     Further, when there is a one to one correspondence between the number of receive symbol streams and the number of Signature control channels associated with these streams, KL (number of SCCMs) must be equal to or exceed L (number of receive symbol streams). In the case where KL exceeds L, a number of the SCCMs may remain unused for reception of Signature control channels, or may be utilized for other purposes such as receiving Signature control channels from individual receive chains. 
       FIG. 5C  is an exemplary block diagram of an embodiment of a Signature control channel modem  510 B-kl. Digitally sampled receive symbol stream DRx-kl is coupled to Signature Control Channel Detector/Synchronizer block  570 C, which preforms timing synchronization with the DSSS signals within the input signal, and detects the presence and associated signal levels (in uncorrelated and correlated levels for example, Io, Ec, Es, Ec/Io and/or, Es/Io), and associated timing information and provides one or more of the determined values to the Modem Timing Controller  550 C. The Modem Timing Controller  550 C, in one embodiment, utilizes the timing and received Ec/Io information to trigger the demodulation and or transmission of Signature control signals respectively associated with the Digital Demodulator  560 C and the Digital Modulator  580 C. The digitally sampled receive symbol stream DRx-kl is additionally coupled to the Digital Demodulator  560 C, which upon receiving SCCM_Ctrl configuration information, and timing information from the Modem Timing Controller dispreads and demodulates the DSSS signals associated with the Signature Control Channel and any associated pilot, and any data sub-channels for SCCM_Data. The SCCM_Ctrl configuration information, in specific embodiments, may contain a specific PN code, Gold code, or other code to be utilized for spreading and dispreading in the SCCM  510 B for use in Digital Demodulator  560 C and Digital Modulator  580 C. Additionally, the SCCM_Ctrl may contain the identity of values of specific orthogonal codes for use with specific sub-channels of a common control channel structure. Such orthogonal codes may include Walsh Codes, CAZAC Codes, Zadoff-Chu codes and the like. Further, the specific codes may be designated as for use with a pilot channel utilized for synchronization and as a phase and amplitude reference for demodulation, and other codes designated for use with specific data sub-channels carrying BPSK modulated data in one example embodiment. Referring to  FIG. 5C , Digital Modulator  580 C provides a modulated control channel signal MTx-kl, upon receiving the mentioned configuration information from the SCCM_Ctrl, the SCCM_Data to be transmitted, and the timing from the Modem Timing Controller  550 C. Either, or both of the Digital Modulator  580 C and the Digital Demodulator  560 C may be disabled utilizing the SCCM_Ctrl signal. 
     As mentioned previously, such DSSS and CDMA transmission and reception approaches and structures are well known in the art including as utilized in the downlink of IS-95, W-CDMA, CDMA-2000 and the like. Further aspects of such art is disclosed in the previously references book  CDMA: Principles of Spread Spectrum Communications , by Andrew J. Viterbi (Addison Wesley Longman, Inc., ISBN: 0-201-63374-1). 
     An alternative embodiment, not shown, of the SLP  500  of  FIG. 5A  may be implemented using in reference to  FIGS. 5B and 5C  a separate bank of Digital Modulators  580 C arranged from 1 to K each with an output MTx-k and respective inputs SCCM_Ctrl-k and SCCM_Data-k, a separate bank of Digital Demodulators  560 C arranged from 1 to L each with an input DRx-l, an associated Detector/Synchronizer  570 C and timing control signals, and respective outputs SCCM_Ctrl-l and SCCM_Data-l, as well as associated DRx bypasses, DTx combiners and modified SLP Controller  520 B as would be apparent to those skilled in the art. 
       FIG. 5D  is an illustration of an exemplary Advanced Backhaul Services (ABS) compliant signal including an in-band and inline signature signal deployed within a single channel. The vertical (y) axis of the figure corresponds to the frequency spectrum, while the horizontal (x) axis corresponds to time increasing from left to right. The bandwidth of the exemplary ABS signal corresponds to the minimum channel bandwidth for the ABS services, corresponding to BW CH_Min . The bandwidth BW CH_min  corresponds to the allocated channelization of the ABS system, in some embodiments to BW CH_Min  may also specify the bandwidth of the signal ( 5 D- 10 , 20 , 30 , 40 , 50 ) occupying the channel as well, while in other embodiment the ABS signal may be fixed at a proportion of this bandwidth, while in yet other embodiments the signal bandwidth may not correspond to the minimum channelization bandwidth in-so-far as the non-signature signal bandwidth does not exceed BW CH_min . In specific embodiments, the signature based alert signal ( 5 D- 20 ,  5 D- 40 ) is related to the minimum channelization bandwidth to BW CH_min , where the non signature based service signal ( 5 D- 10 , 30 , 50 ) may or may not correspond to the minimum channelization bandwidth BW CH_Min . In this context, “in band” indicates that the signature based alert signal  5 D- 20 , 40  (or a alert signal in general) is transmitted within the same frequencies of operation as the user payload information signals ( 5 D- 10 , 30 , 50 ). Additionally, in the current embodiment, “in-line” indicates that the user payload signal ( 5 D- 10 , 30 , 50 ) and the Alert signals ( 5 D- 20 , 40 ) are time multiplexed together, and transmitted “in-line” with each other. In the current embodiment, specific conventions or rules are followed so as to allow a receiving station adhering to the ABS system to detect and demodulate the alerts from another station. Embodiments of the ABS system allow for such detection and communication even between ABS compliant devices not engaged to direct communication utilizing the user payload signal ( 5 D- 10 , 30 , 50 ), or even able to receive and process such user payload signals due to devices being from different manufacturers or having incompatible configurations in hardware software, or management. A pre-determined arrangement of BW CH_min , and/or other system parameters allow for even non-compatible equipment to detect and receive information to allow for knowledge relating to the presence and potentially operating parameters of other information associated with other ABS stations within the propagation range for which interference may be a problem. Further, as will be discussed further, such ABS compliant stations in some embodiments may be able to not only detect such signatures but also respond with transmissions so as to allow for intercommunications between two ABS compliant stations. This intercommunication can then occur even for stations in which it is either undesirable or even physically impossible to intercommunicate amongst directly using the user payload signal ( 5 D- 10 , 30 , 50 ). 
     In a related embodiment, inline signatures/alerts  5 D- 20 , 40  are sent at the maximum allowable transmission power of the transmitter. In other embodiments, the alerts (inline signatures  5 D- 20 , 40 ) are transmitted at the same average transmission power level as the composite ABS information signal ( 5 D- 10 , 30 , 50 ) it is inline with, during the inline transmission period. Other embodiments may provide for the alert transmission power to be set at a ratio relative to the user information signals ( 5 D- 10 , 30 , 50 ), or the like. 
     For some embodiments using inline, in-band communications, timing constraints related to the transmission of the alert signals are required, but may allow flexibility within a pre-defined window. In one embodiment, it is undesirable to require a fixed periodicity for the inline signature. Such an arrangement may be too rigid for specific embodiments. In such an embodiment, inline transmission periods could be:
         i. Shorter than T Max   Alert      ii. Longer than T Min   Alert      iii. where T Max   Alert =T Min   Alert +T VALID   Alert          

     Referring again to  FIG. 5D , T VALID   Alert  represents the period of time in which the transmission, or the detection of an alert is possible. T Max   ALERT  represents the maximum duration in time since the detection of the last alert (or in other embodiments another time reference or event) that an alert may be received, or expected. T Min   ALERT  represents the minimum time (e.g. the soonest) for which an alert may be expected or allowable to be transmitted since the last alert (or in other embodiments another time reference or event). T Actual   ALERT  represents the actual time between alerts (or in other embodiments another time reference or event). Other “events” may include, but are not limited to, the reception of other signals such as alerts for other ABS compliant systems, or an absolute time reference, GPS time, IEEE1588 time references, or the reception of another signature within the ABS compliant transmission signal, which triggers such a relationship to an alert reception timing. The various T X   ALERT  parameters may be coded within ABS devices (or known a priori), or retrieved from the registry server (based upon geographic location or region for example, or based upon ABS station identification in another example), broadcast by ABS devices, or retrieved from a look up table. Such parameters may be usable, in one embodiment for both inline alert processing, but also embedded alert processing, while in another embodiment usable for transmission and reception on the common control channel—out of band. 
       FIG. 5E  is an illustration of an exemplary Advanced Backhaul Services (ABS) compliant signal including an in-band and inline signature signal deployed within multiple channels. In this embodiment, an example of an ABS compliant system utilizing multiple channel for transmission and reception is depicted. 
     BW signal  represents the entire bandwidth, or equivalent number of occupied minimum channels BW CH_Min  in use by a specific ABS compliant system, in one embodiment. In this embodiment, the modulation symbol rate of the user information signal  5 E- 10 , 30 , 50  will be proportionally faster (by the ratio of BW_Signal/BW CH_Min ) than that of the alerts ( 5 E- 20 A-D, 5 E 40 A-D). This is because the individual alert signals ( 5 E- 20 A-D, 5 E 40 A-D) in this embodiment are sent in a manner consistent with those sent for an individual channel as depicted in  FIG. 5D , as alerts  5 D- 20 , 40 , and each will occupy an individual bandwidth BW CH_Min . In the current embodiment, however, the modulated symbols for the information payload signal  5 E- 10 , 30 ,  50  occupy the entire BW signal  and have a proportionally shortened symbol period in a single-carrier modulation scheme or a proportionally increased number of carriers in a multi-carrier modulation scheme. Other embodiments may utilize individual information carrier signals of the same modulation symbol rate as the alerts, and form a multicarrier signal as an alternative, so as to provide a plurality of the signals depicting in  FIG. 5D , but in a multiple carrier arrangement of  FIG. 5E . In yet other embodiments, a combination of multicarrier information signals and individual information signals of varying bandwidths may be utilized. In one embodiment, despite one or more arrangements of signal information bandwidths within BW signal  the bandwidth of the alert signals will be the same or similar as that depicted in  FIG. 5E . In other embodiments, there may be a set of possible alert signal bandwidths. 
       FIG. 5F  is an illustration of an exemplary embodiment of Advanced Backhaul Services (ABS) signature signals of various structures. Referring to row A, an alert signal  5 F- 10  is of length L ALERT  In the example embodiment of row B, a single signal  5 F- 20  is depicted of length L SIG  In this embodiment, L SIG  is equal to L ALERT . In the embodiment of row B, the alert signal  5 F- 20  includes two signature code sequences, one modulated on the in-phase channel (I) and another modulated on the quadrature phase channel (Q) of a QPSK modulator, as is known by one skilled in the art. Such an arrangement allows for the two sequences to be respectively individually modulated by signature information bits S(0), and S(1). The present embodiment can support a number of different modulations including, for example, coherent BPSK as described herein. In one embodiment, the I code sequence and the Q code sequence are not the same, and allow for detection utilizing individual correlators as will be discussed. For example, when S(0) is equal to S(1), the resulting information bit is interpreted as a “0”. On the other hand, when the correlated values of the are opposite sign (for example, when S(0) results in a positive correlation value, and S(1) results in a negative correlation value) the resulting information bit is interpreted as a “1”. Many other arrangements and variations may be used as well, consistent with coherent modulation techniques. In one embodiment, the in-phase information bit S(0) may be transmitted as a 1, and treated as a pilot signal or symbol, whereas the quadrature information bit S(1) may be interpreted as the payload information signal. Other arrangements are possible as well, allowing for other modulations such as QPSK, and m-ary QAM modulation. The signature code sequences I and Q may be any number of types of codes as known in the industry and as discussed. In one embodiment, the I and Q codes are two codes orthogonal to each other, such as may be produced utilizing a maximal length code (m-sequence or m-code), and modulated by two different Walsh codes as in known. In yet further embodiments, alternative orthogonal codes may be used such as so called CAZAC codes, or Zadoff-Chu codes. In yet another alternative embodiment, the I and Q codes may be multiple codes, each having a plurality of Walsh codes, where one set for I and Q includes a code division multiplexed pilot reference signal with pre-determined values of ones (for example) for the polarity of both the I and the Q Walsh codes of the pilot channel, and the third and fourth codes are the codes associated with S(i) and S(i+1) for the alert sequence. Of course, the I and Q Walsh codes may be re-used for each of the two I and Q Walsh codes, but with a third Walsh code applied to one of the I/Q sets so as to produce a third and fourth orthogonal code. In the current embodiment, all four Walsh, or other orthogonal codes may then be “covered” or scrambled on a chip by chip basis with an alert code, such as m-sequence, gold code, a portion of these, or the like. 
     Alternatives not utilizing orthogonal codes are possible as well, for instance using two different m-sequences for each of the I code and the Q code where the length of each m-sequence is equal to L SIG  and includes the signature sequence(s). Alternative codes which may be utilized include Barker codes, gold codes, and others and known in the art. 
     Referring now to the embodiment of row C, two sets of signature sequences  5 F- 30 A,  5 F- 30 B are sent per one alert time period (L SIG =½*L ALERT ) Each signature information bit S(n), where n=0 to 3, may be utilized so as to produce a number of different modulation formats including both coherent modulations, and differentially encoded modulations. Some example modulations utilized in various embodiments include DBPSK and DQPSK using differential encoding; and BPSK, QPSK, QAM utilizing a phase reference such as a pilot bit, pilot symbol or pilot channel). Various codes and modulation structures may be utilized as described in the foregoing. 
     Row D of  FIG. 5F  depicts a similar arrangement as row C, except where N sets of signature code sequences ( 5 F- 40 A to  5 F- 40 N) are depicted allowing for 2*N information symbols S to be utilized. The current embodiment includes code sequences of length 
     
       
         
           
             
               L 
               SIG 
             
             = 
             
               
                 1 
                 N 
               
               * 
               
                 
                   L 
                   ALERT 
                 
                 . 
               
             
           
         
       
     
       FIG. 5G  is an illustration of an exemplary Advanced Backhaul Services (ABS) compliant signal including an in-band and embedded signature signal. The previous figures  FIG. 5D ,  FIG. 5E  and  FIG. 5F , depicted “inline” alerts as discussed. As an alternative, in band embedded alerts may be utilized. Similar embedded signaling was first introduced in co-pending application U.S. Ser. No. 13/763,530, the entirety of which is incorporated herein by reference. The term embedded is used in the current context to describe an alert signal  5 G- 25 ,  5 G- 35  which is not time multiplexed with the payload information bearing signal  5 G- 10 ,  5 G- 30  but is present at the same time as the payload signals during specific periods of time. In this embodiment, the transmission  5 G- 25  during a T VALID   ALERT  period includes a plurality of individual alert signals  5 G- 25 A through  5 G- 25 H, each of length L ALERT  such that transmission  5 G- 25  is referred to as a composite embedded alert signal. Likewise, the composite embedded alert signal  5 G- 35  includes a plurality of individual alert signals  5 G- 35 A through  5 G- 35 H. The repetition of the identical individual alert signals making up each composite embedded alert signal is performed so as to compensate for a reduced transmission power level P Emb   ALERT  relative to the transmission power level for the payload information signal  5 G- 10 , 5 G- 30 . The time period in which alerts may be received, as explained previously, is denoted TAPE and encompasses the entire composite alert sequence  5 G- 25 , and respectively  5 G- 35  in a separate valid period. In the current embodiment, the information carried within  5 G- 25  and  5 G- 35  is different. Within a given composite embedded alert signal, the individual alert signals are the same and each individual alert signal includes one or more modulated information bits (such as S(0) through S(2N−1) of  FIG. 5F .) Thus, the individual information bits within a given composite alert signal remain the same so as to allow further processing such as coherent combination of the individual alerts  5 G- 25 -A through  5 G- 25 H within composite alert signal  5 G- 25 . Such coherent combination processing results in compensation for the reduction of the transmitted power level of the alerts relative to the payload information bearing signal by the amount P Emb   ALERT  In one embodiment, N embedded alert signatures may be transmitted at P MAX −10*log 10 (N), or in yet other embodiments, a power level based upon such as calculation. Further in such an embodiment, the N embedded signatures may be transmitted sequentially such that coherent combination is possible over T VALID   Alert . 
     In order to prevent the combination of individual alerts of different composite alert signals  5 G- 25  and  5 G- 35 , a gap of time between the T VALID   ALERT  periods is defined so as to ensure only individual alert signals of the same composite alert signal are combined together. The spacing between successive T VALID   ALERT  periods are defined by T Min   ALERT  and T Max   ALERT  as previously discussed, and depicted within  FIG. 5G . For both the inline and the embedded embodiments of the alert signals, the use of a window of time T VALID   ALERT  for the transmission of alert signals and/or composite alert signals provides for some flexibility, in some embodiments, as to the exact transmission start time of the alert transmissions allowing for the alignment of the transmissions so as to be convenient with other signaling such as a frame timing, start of frame, end of frame, super-frame, or other structure of the payload carrying ABS signal itself. Alternatively such flexibility may allow for the avoidance of transmitting alert signals at a time when it is not advantageous to the ABS payload signal, such as when particularly time sensitive information is being transmitted, when noise sensitive signals are being transmitted such as channel estimation reference signal(s), or other phase references, or to avoid the disruption of the payload signal framing, segmentation, or other grouping of the information signals. As a result, in one embodiment, valid alert transmission T ALERT   VALID  periods must be:
         i. End prior to T Max   ALERT  from the beginning of the previous alert transmission.   ii. Begin after T Min   Alert , from the beginning of the previous alert transmission.   iii. where T Max   Alert =T Min   Alert +T VALID   Alert          

     In embodiments of an ABS system utilizing embedded signatures, the embedded alert signals will act as noise to the user payload bearing signal ( 5 G- 10 , 5 G- 30 ). In some embodiments, the alerts have a code length k providing a “processing gain” resulting from a correlation in a receiver of 10*log 10(k), as previously discussed. If k is sufficiently large, the alert signal(s) may be transmitted at a relative power level reduction P Emb   ALERT  such that the interference resulting form the embedded signal is manageable with no further processing. For example, if the modulation for the ABS payload information signal requires 25 dB of signal to noise and interference 
     
       
         
           
             ( 
             
               S 
               
                 N 
                 + 
                 I 
               
             
             ) 
           
         
       
     
     to be demodulated with a reasonable error rate, an interference level 10 to 20 dB below this level (I Margin ) would be appropriate. Note that within this discussion the term SNR may be understood to include interference as well, and the interference aspect may not be explicitly mentioned in every instance. As a result of the desired SNR for the demodulation of the ABS information payload signal, within this embodiment, the power of the alerts would be set to a value below the payload information signal by P Emb   ALERT =25 dB+I Margin . This relationship assumes that the “chip rate” of the alerts, is comparable to the symbol rate (or sample rate) of the ABS information signal within the relevant channel bandwidth. In contrast to the SNR considerations for the payload information bearing ABS signal, the received alert signals must also be detected with a sufficient SNR, which is an opposing motivation. In general, for a high probability of detection of the signatures, any metric utilized to perform detection should have a signal to noise ratio allowing for an acceptably high probability of detection and an acceptably low probability of false detection. One approach to achieving a high probability of detection is to transmit the alerts signals at a higher level, thus impacting the SNR of the information-bearing signal. However, the relative transmission power of the alert signals in the current embodiment is set by P Emb   ALERT =25 dB+I Margin . 
     A discussion of the signal to noise ratios associated with the probability of detection and false detection may be found in  CDMA: Principles of Spread Spectrum Communications , by Andrew J. Viterbi (Addison Wesley Longman, Inc., ISBN: 0-201-63374-1) pages 48 to 52 and elsewhere. In some embodiments, the resulting signal used to determine detection of the embedded composite alert signals will be the result of the correlation of the individual alerts, and then the combination of the individual alerts into a signal detection signal, which will be used for a detection hypothesis, against a metric. Just as the alert sequences act as noise to the demodulation and successful detection of the information symbols of the ABS information signal, the information signal will act as noise to the successful detection and demodulation of alert signals. Therefore, the processing gain (e.g. the length of the alert signature k) must be sufficiently long, in some embodiments, so as to provide an alert detection SNR that allows for an acceptable probability of detection and a sufficiently low probability of false alarm, associated with the transmission of the alert signatures P Emb   ALERT  dB below the information payload signal. 
     In one embodiment, a detection hypothesis for alert signals is based upon a ratio of the correlated to uncorrelated energy of the alert sequences. Such a test has the added benefit of reducing false detections in the presence of very strong uncorrelated signal levels in contrast to a test based upon correlated energy exceeding a threshold. An example of one such test is based upon the following hypothesis: 
     Alert detection Det(h), if 
     
       
         
           
             
               
                 
                   
                     
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                           = 
                           
                             N 
                             MaxAlerts 
                           
                         
                       
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                       ⁢ 
                       
                         
                           
                             P 
                             DET 
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                           ⁡ 
                           
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                             P 
                             DET 
                             AlertUncorr 
                           
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     where,
         Receivers must integrate for N MaxAlerts , where N MaxAlerts  is equal to the maximum number of alerts which are possible within the time window T VALID   ALERT , and for each h.   h is the alert code sequence(s) start time under the current hypothesis being tested.       

     The above test allows for the detection of either inline or embedded alerts with a certain probability P Detect   Alert  of detection, and a certain probability of false detection P False_Detect   Alert . Such a process requires performing the above test over all possible start times of the alert signal within T VALID   ALERT . 
     While the forgoing discussion includes embodiments for embedded alerts, which balance the transmitted alert signal power with interference to the ABS information signal, alternative embodiments allowing for a higher transmission power of the alerts may be utilized which provide for both a higher alert transmission power, and maintaining the SNR of the ABS information payload signal at the intended receiver(s), through the use of interference cancellation at the intended receivers. Despite such an alternative, the detection hypothesis test of Eq. 5-1 may be utilized with interference cancelation at the receiver as well. 
     Interference cancelation in this context provides for subtracting a known undesired interfering signal from a total received signal to result in a remaining signal that has an improved SNR. The use of embedded alerts is one such situation allowing for the use of interference cancelation at a receiver attempting to receive the ABS information payload signal because the signature(s) (the exact codes) of the alerts are known a priori to the reception of the signal as having been defined as part of the overall system, or communicated as part of an overhead message of some sort between the transmitter and the receiver. Further, the power level relationship and likely the phase relationship between the information signals and the alert signals may be known as well in some embodiments. In general, each “unknown parameter” such as amplitude, phase, information signal, code sequence, etc., are estimated to allow the generation of an estimated interfering signal to allow for the actual interfering signal to be cancelled utilizing a subtraction of the estimated interfering signals from the total signal where the total signal contains the actual interfering signal (or signals). The more parameters that are known before hand (such as code sequence, amplitude, phase, and timing) the fewer parameters require estimation, thus reducing the complexity and opportunity for error in an implementation at a receiver. Such processing (an interference canceller) may be implemented in some embodiments after down conversation, digitization, and spatial processing, but prior to demodulation of an individual stream. For example referring back to  FIG. 5A , an alert signature signal cancelation processor may be implemented, in one embodiment, within the Signature Link Processor  500 . Utilizing an interference cancelling Signature Link Processor embodiment would allow for an increased performance of the detection of alert signals as the alert signals may be transmitted at a level relative to the ABS information signal which would not allow sufficient SNR for the demodulation of the ABS signals without interference cancelation in specific embodiments. Further, such an arrangement in embodiments, may allow for an enhanced security between a transmitter and receiver of the same link, providing for known parameters to be shared for use in the interference cancelation “parameter estimation” process. In such an arrangement, one feature of enhanced security comes from the fact that the shared parameters may be modified occasionally, or continuously with such knowledge only being shared between the transmitter and receivers of a trusted link(s), which other receivers would require full estimation, and which may prove challenging in specific embodiments. Further, the use of such parameters by a receiver may be used, in specific embodiments, as a form of authenticity check to confirm the continual identity of the transmitting station. 
     Embodiments of structures for receiving and transmitting alert signatures, and signals were, in part, described associated with  FIGS. 5A, 5B, and 5C . Further details, and embodiments of functions associated with the Signature Control Channel Detector/Synchronizer  570 C and the signature Control Channel Digital Demodulator  560 C of  FIG. 5C  will now be described. Additionally, embodiments capable of detecting and demodulating either inline or embedded signatures within a single receiver structure are also described. Alternative embodiments requiring a dedicated receiver for one or both the inline and the embedded alert signals are contemplated as well. 
     In some embodiments where a device must be able to detect both an inline and an embedded signature signal using a single receiver structure, it is contemplated that the chip rates of the inline and the embedded are to be the same, and only the power level versus repetition number be different. In related embodiments, the detected alert power ideally would result in the same or a substantially similar level, independent of the alerts being embedded or inline. Such embodiments may allow for determining information relating to the received level of the ABS information payload signal based upon the detected alert signal level. Such information, in specific embodiments allow for an assessment of the potential for interference with or from the transmitting ABS station as discussed previously. 
       FIG. 5H  is an exemplary block diagram of an embodiment of a Sliding Correlator (CS). The depicted embodiment of the sliding correlator  5 H- 10  is implemented within a finite impulse response filter (FIR)  5 H- 20 , whose correlated output is effectively the channel impulse response of the wireless propagation channel between a transmitted signature and the sliding correlator&#39;s associated receive symbol stream from IBR Channel MUX  328 A of  FIG. 5A  or associated receive chain output from IBR RF  332 A of  FIG. 5A . The sliding correlator  5 H- 10  additionally outputs noise as a result of correlation with “uncorrelated” inputs such as signal from the ABS information payload signals ( 5 D- 10 ,  5 D- 30 ,  5 D, 30   5 E- 10 ,  5 E- 30 ,  5 E- 50 ,  5 G- 10 ,  5 G- 30 ), and uncorrelated interference from other transmitters, as well as from receiver front end thermal noise sources and the like. This input to the sliding correlator may be, in one embodiment, the DRx-kl of  FIG. 5C , and the sliding correlator is within one or more of blocks  560 C, and  570 C of  FIG. 5C . In the current embodiment, FIR  5 H- 20  is a complex FIR, receiving complex input, and FIR filter coefficients from Code Register/Input  5 H- 30 . To the extent that the alert signature code(s) are real valued, the code provided by  5 H- 30  may be real valued as well. For complex values codes such as Zadoff-Chu codes, the code register  5 H- 30  provides the complex valued code to the FIR filter  5 H- 30 . In one embodiment, a complex code provided by code register  5 H- 30  includes one Walsh code chosen from a set of orthogonal Walsh codes for the real portion of the code input to the FIR  5 H- 20 , and another Walsh code, different from the first Walsh code but from the same set of Walsh Codes as the imaginary input to the complex FIR filter  5 H- 20 . In another embodiment, two different Barker codes of the same length are provided to the real and imaginary code inputs. In another embodiment, two different m-sequences of the same length, or portions of a longer code of the same length are provided to the real and imaginary code inputs. In one embodiment, the output of the sliding correlator  5 H- 10  as described above will provide the complex impulse response of the correlated signal transmitted through a wireless channel to the receiver as modified by the instant multiplexing settings of IBR Channel MUX  328 A of  FIG. 5A . 
       FIG. 5I  is an exemplary block diagram of an embodiment of a Complex Sliding Correlator Block (CSCB). In one embodiment, two sliding correlators  5 H- 10 A and  5 H- 10 B are used with a single complex valued input, but with different codes including a pilot channel based upon a in-phase and quadrature set of Walsh codes (for example, W0 and W1), and a data channel having two other Walsh codes (for example, W2 and W3), wherein the set of Walsh codes is chip by chip covered by a gold code to form Sequence Set j (SSj). Two of the codes within SSj, denoted as S1 and S2 (for Pilot I and Q, and respectively including W0 and W1) are provided to SC  5 H- 10 A, and the other two codes, denoted as S3 and S4 are provided to SC  5 H- 10 B (for the data channel). The complex output of the two sliding correlators (SCs) are provided as respective outputs, as well as respectively squaring them (utilizing blocks  5 I- 20  and  5 I- 30 ) to determine the magnitude squared of each, which are then summed together at  5 I- 40  for use in the detection hypothesis of Eq. 5-1 (as Mag{circumflex over ( )}2 or alternatively as Mag via SQRT—square root—block  5 I- 20 ). The Mag{circumflex over ( )}2 produced by block  5 I- 30  provides a value proportional to the power term “P” required by EQ. 5-1. Compensation for the proportionality may be made by adjusting the TH DET   ALERT  value appropriately to compensate for any impedance value of the Mag{circumflex over ( )}2 measurement, relative to a value required for an exact power measurement. In alternative embodiments, for instance, where the S(0) provides the phase reference and S(1) provides the data values (as described associated with  FIG. 5F  Row B for example) the code sequence set (SS(j)) is composed of only two codes, one for each of the two sliding correlators. The sliding correlators, in this embodiment are correlating an incoming complex signal with a single real code (each of which includes two real FIR filters for performing correlations in this embodiment.) 
       FIG. 5J  is an exemplary block diagram of an embodiment of a Sliding Detector (SD). Sig(n) are time samples of the complex (I and Q) values indexed by the variable n of receive signal. In one or more embodiments, Sig(n) are DRx-kl of  FIG. 5B  and  FIG. 5C , where kl may vary from 1 to KL. In some embodiments Sliding Detector  5 J- 10  includes functionality included within signature Control Channel Modem  510 B-kl. In other embodiments, Sliding Detector  5 J- 10  is within signature Control Channel Modem  510 B-kl. 
     Sliding Detector  5 J- 10  includes CSCB  5 I- 10 . The sequence set (SSj) is provided by the Sliding Detector Control input, which provides additional control inputs in various embodiments. The Mag and Mag{circumflex over ( )}2 outputs of  5 I- 10  are provided, in one embodiment, as outputs of Sliding Detector (SD)  5 J- 10 , and as outputs of the CSCB  5 I- 10 . Other embodiments of a Sliding Detector  5 J- 10  and/or CSCB  5 I- 10  may have only one or neither of such outputs, potentially depending upon the embodiment of detector/demodulator, such as  5 K- 00  of  FIG. 5K, 5L-00  of  FIG. 5L , or Signature Control Channel Modem  510 B- 1  of  FIG. 5B . Other outputs of the CSCB  5 I- 10  of Sliding Detector  5 J- 10  include the complex output XC_Si_A(n), which is a function of the discrete time index n, and is coupled to conjugate block  5 J- 40 , via in-phase and quadrature (real and imaginary) lines to a complex numerical representation (in the current embodiment). Such a conversion is often ignored in general block diagram representations, and may be considered inherent in some embodiments, or integrated with another functional block. 
     Additionally, in the current embodiment, output XC_Sj_B(n) is provided to complex multiplier  5 J- 50 . In certain embodiments, the conjugated signal from  5 J- 40  represents the phase (mathematically conjugated) of the received signal for a pilot CDMA channel derived from a correlation with the CSCB using one or more orthogonal codes (as described above in one embodiment), and providing for a demodulation of a pilot code channel. Further, the signal resulting from  5 J- 30  may represent a data CDMA channel resulting from the CSCB  5 I- 10  utilizing one or more other orthogonal CDMA codes, potentially including one or more “cover” PN scrambling codes (again as described in the foregoing on one or more embodiments). In such an embodiment, using a CDMA pilot code channel and CDMA data code channel, the de-spread and de-multiplexed information symbol SMj(n) is provided as an output of the Sliding Detector  5 J- 10 . 
     In another embodiment, where a coherent pilot signal is provided to the in-phase portion of the transmit signal (as S(0) of  FIG. 5F  of Row B for example), and a modulated (BPSK) symbol is provided to the quadrature signal during modulation (as S(1) of  FIG. 5F  of Row B for example) only the imaginary portion of the de-spread, and phase re-rotated signal is provided to the output of the Sliding Detector  5 J- 10 , for further processing. In another embodiment shown in  FIG. 5J , the demodulated and phase de-rotated signal is provided to the Sign function  5 J- 70  prior to output as Dj(n), which may be considered a “slicer” providing for any value greater than or equal to zero as a positive 1 digital output, and any value less then zero as a digital zero output. The configuration of the specific codes and associated processing is configured by the Sliding Detector Control input. 
       FIG. 5K  is an exemplary block diagram of an embodiment of an inband inline signature detector, wherein the forgoing embodiments may be demodulated and detected. The set of signals provided by the Sliding Detector is designated as Vj(n), where n is a discrete time index for the resulting “convolution” of the FIR filter codes in Code Register/Input  5 H- 30 , with the input signal  5 K- 02 , and the associated processing of the various embodiments discussed. In one embodiment, the Vj(n)=Dj(n), SMj(n), Magj(n), Mag{circumflex over ( )}2j(n). Other embodiments may provide a subset, or a superset of the signals included as Vj(n). V(j) is then passed as an input to the Detection Logic block  5 K- 30 , where the Magj(n), and/or Mag{circumflex over ( )}2j(n) is utilized (or even locally derived in some embodiments) so as to perform the detection of the signal, and identification of the signal or signal multipath components for use with demodulation. For example, one approach to detection would be to determine the first signals to exceed a threshold. Another example embodiment uses the maximum or “peak” signal above a threshold. A yet further embodiment, with more optimal performance, provides for the coherent integration (simple real values summed, and imaginary values summed respectively of SMj(n), or Dj(n) for embodiments where the Sign  5 J- 70  is not performed on the signal) of all values having a magnitude or Mag{circumflex over ( )}2 above a threshold. Such an embodiment may be considered an optimized form of a so-called “rake receiver”, or matched channel filter. Such an arrangement is advantageous as all the values of SMj(n) which are above a threshold have been de-rotated and aligned in phase allowing for coherent integration. There are a number of approaches that are contemplated for detection within the processing of  5 K- 30  Detection Logic. In one embodiment, all the values of Vj(n) are stored, and information useful for determining the threshold for the current and/or future values of Vj (n) (or V (j+1) (n) for example) are utilized alone or by interacting with Detector Controller  5 K- 40 . In other embodiments, only a subset of values of Vj(n) are stored and/or values derived from Vj(n) associated with statistics for setting the detection thresholds, and the resulting detection values. Additionally, the demodulation “slicing” of an information symbol resulting from processing of SMj(n) for example may be performed to result in demodulated bit(s) associated with M-ary QAM modulation (including BPSK, QPSK, and higher order modulation symbols). 
     In one embodiment, the slicing of the detected modulation symbol is not performed within  5 K- 30  but performed in a subsequent block, such as Detector Controller  5 K- 40  or elsewhere in the IBR. 
     Coherent demodulation has been described in forgoing embodiments, but in various embodiments, Detector Controller  5 K- 40  and/or Detection Logic  5 K- 30  may perform differential demodulation as well, such as DQPSK, DBPSK. For example, the Detection Logic  5 K- 30  may store symbols for differential processing. In yet additional embodiments, a single code may be used rather than two in some embodiments of differential modulations. 
       FIG. 5L  is an exemplary block diagram of an embodiment of an in-band detector Signature detector useful for either inline or embedded alert signals using repeated codes as described associated with  FIG. 5G  and related embodiments. The blocks of  FIG. 5L  are capable of operating in an analogous manner to the blocks of  FIG. 5K  for inline signature operation. For embedded alert signal operation with the repeated signature codes (such as depicted in  FIG. 5G ) the replicated blocks of  FIG. 5K  will operate in a similar way in some embodiments. However, for embedded and repeated signatures, a coherent integration of each phase de-rotated symbol will be performed utilizing Vj(n) summed, via summer  5 L- 10 , with the contents of Memory  5 L- 20 . Upon initiation of the receive detection process, Detector Controller  5 L- 40 , in one embodiment, will clear the contents of Memory  5 L- 20  to all zeros. Alternatively, Summer  5 L- 10  may be controlled so as to not include the output VIntOut(n)  5 L- 22  during a first integration pass effectively adding zeros to the incoming Vj(n) values and outputting VSum(n) to be stored in respective memory locations of Memory  5 L- 20  indexed by n, and under the address control of Detector Controller  5 L- 40 . In one embodiment, the Memory  5 L- 20  is of sufficient size so as to store all values from the repetition of the signature, within directly using the summer  5 L- 10  during real time processing. In alternative embodiments, the phase de-rotated, “matched filter outputs” are stored in Memory  5 L- 20 , and iteratively summed with the previously de-rotated matched filter outputs so as to perform coherent integration on a repeated code by code time scale (as described associated with  FIG. 5G  and for example using repeated codes  5 G- 25 -A through  5 G- 25 -H), thereby repeating through the addresses in the memory once for each signature repetition as aligned to the beginning of each corresponding output of the Sliding Detector  5 I- 10 . In an alternative embodiment, phase de-rotation by complex multiplier  5 J- 50  may be bypassed and the CSCB  5 I- 10  XC_Si_A, and B may be coherently integrated within the Memory  5 L- 20 , and phase de-rotation performed after integration, by detection logic  5 L- 30  for example. Additionally, in the various embodiments, Detection Logic  5 L- 30  would perform the Mag or Mag{circumflex over ( )}2 function period to the detection processing and threshold determination processing associated with the discussion relating to embodiments of Detection Logic  5 K- 30 , and should be considered applicable to the current embodiment. Such processing, in some embodiments, includes the channel matched filter coherent integration processing associated with the forgoing discussions. The threshold processing in specific embodiments may be performed utilizing equation Eq. 5-1. The determination of the uncorrelated values may be achieved by summing values below a specific threshold from a peak or maximum value, or may be based upon correlating with a code which is known not to be utilized. In some embodiments, the uncorrelated values may be based upon the output of the sliding correlator or related processing for times in which the reception of alerts is determined to be unlikely, for example between T VALID   ALERT  periods. In yet further embodiments, statistical methods to determine periods without alerts and periods including alerts so as to set a threshold for detection. 
     The timing of the addressing may be determined and may be adjusted by monitoring detections performed by the Detection Logic  5 L- 30  in combination with Detection Controller  5 L- 40 , thereby allowing for the synchronization and tracking of the T VALID   ALERT  periods and the appropriate aligning of the associated times so as to allow for coherent integration. Further, an intermediate threshold, in some embodiments, may be performed so as to allow for a determination of the current number of alert signature repetitions to include within the coherent integration, thereby individually detecting each repetition, or a subset of repetitions. Some embodiments may include a more robust information field allowing for the explicit signaling of the number of repeated signatures to be determined form the signal itself. In at least one embodiment, the number of repetitions is known a priori, and in yet other embodiments, the number of repetitions and other information related to the modulation format or timing of transmission is determined from the central registry ( 4 C- 60  and/or  4 C- 70  of  FIG. 4C ) or another data base (such as Private Database  440 , IBMS Private Server  424 , IBMS Global Server  428 , Public Database  452 , or Proprietary Database  448  of  FIG. 4G ). 
       FIG. 6A  is an illustration of an exemplary Advanced Backhaul Services layered control link communication protocol stack. The figure is divided into two vertical columns, denoted by Control Plane and User Plane. The User Plane is for use by the IBR and/or the IBMS, in various embodiments, for the delivery of messages to peer entities (or their equivalents). One example of the use of the User Plane is interfacing to the Registry via other ABS devices. In another example, generic IP packets are passed over the User Plane Protocol. The User Plane&#39;s ABS protocol stack of  FIG. 6A  begins with the ABS Packet Data Convergence Protocol (ABS PDCP). In some embodiments, the operation of the Control Plane and the User Plan is generally similar from the PDCP layer and below with a few exceptions. The ABS PDCP will be discussed below. 
     The Control Plane is responsible for ABS relegated operation involving the procedures and associated messaging required to be compliant with the ABS Rules as previously discussed, and will be discussed in specific examples associated with subsequent figures. 
     ABS-ME (management entity) is the highest portion of the ABS Control Plane, and is responsible for topology management, processes management, configuration, and interfacing to other ABS peers. The ABS ME interfaces to various “host” radio entities (IBR/IMBS entities in some embodiments), including interfaces to IBR-RLC, IBR-RLP, and even IBR-MAC for timing in some embodiments. 
     The ABS ME further interfaces to other ABS stack entities as well to perform required functions in some embodiments. In some embodiments the ABS ME interfaces to other layers directly, while in other embodiments associated sub-layers are called upon to interface to the required ABS stack sub-layer. For example the ABS-ME configures/controls MAC to scan for interference, in one embodiment directly, and in other embodiments utilizing the ABS RRC. In the non-limiting subsequent example discussion, it will be assumed that each layer interfaces with the layers directly above or below the layer under discussion. It should be noted that other embodiments may interface in various other ways, including directly between non adjacent layers. 
     Returning now to the discussion of the ABS ME, example functions performed include: configures/controls MAC to broadcast signature, interfaces to IBR IBMS Agent, interfaces to ABS-RRC to send standardized messages to other ABS-RRC entities, requests ABS specific procedures from the ABS-RRC, such as so-called—“progressive interference” or “blooming”. These procedures will be discussed in more detail associated with subsequent figures. 
     The ABS Radio Resource Control (RRC) interfaces with the ABS-ME and the ABS PDCP to perform services including control/peer messaging, state management, ABS message composition, and interfaces with other ABS-RRCs. 
     The ABS Packet Data Control Protocol (PDCP) interfaces with the ABS RRC to: arbitrate user plane and control plane priority for access to the ABS-RLC, perform “RLC “Framing” by adding a ABS-RLC header, “whitens the payload” (no  6  sequential is in a row for example), and Ciphering (encryption). The ABS-PDCP Message header addition includes a synchronization field (for example “111111”) and a logical channel index of 2 bits. The logical channel indication includes (as one example embodiment):
         00—EOP (End of Packet)   01—ABS RRC (Control Plane)   10—ABS UP (User Plane)   11—reserved       

     The ABS Radio Link Protocol (ABS-RLP) interfaces to the ABS-PDCP and the ABS-MAC to provide services to the ABS_PDCP and higher layers. Functions performed by the ABS-RLP include: 
     Fragmentation into N bit PDUs, where in one embodiment N=1 for inband and N&gt;1 for out-of-band fragmentation. Other embodiments may provide for inband signaling utilizing N&gt;1 through the use of higher order modulation, and/or multiple alert sequences such as embodiments as described associated with  FIG. 5F  rows C and D. 
     Forward error correction (FEC) 
     Cyclic Redundancy Check (CRC) 
     The ABS Media Access Control (ABS-MAC) interfaces with the ABS-RLP and ABS-PHY layers to provide services to the higher layers. The ABS MAC, in specific embodiments, performs the following example functions: 
     Transmission/reception timing 
     Out of band access to the media (listen before talk for out of band) 
     In-band signaling access to the media 
     The ABS physical layer (ABS-PHY) interfaces with the ABS MAC to perform (in one embodiment) the following example functions: 
     Transmission/reception 
     Modulation/Demodulation using 
     Interfacing with one or more of channels/formats: 
     Out of band: Common Control Channel 
     In-band inline, 
     In-band embedded 
       FIG. 6B  is an exemplary block diagram of an embodiment of an Advanced Backhaul Services control link protocol processor. In one embodiment of the control link processor, the ABS-MAC is within processor  6 B- 50 , which interfaces to various other entities including the IBR RRC, IBR RLC, and IBR MAC to derive timing and coordinate activities. In one embodiment, the ABS-RLP is contained with a separate processor, and an interface to and from the RLP is provided. In alternative embodiments, several or all the stack functional entities are within Processor  6 B- 50 . In an exemplary embodiment wherein at least the ABS-MAC is contained within the Processor, additional functional entities are interfaced, including a Random Number Generator  6 B- 20 , Clock  6 B- 30 , and one or more timers within Timer module  6 B- 40 . The Clock and Timer functions, in various embodiments, are used to determine transmission timing such as T VALID   ALERT , and the Alert transmission periods for example, as well as being utilized for other functions. The Random Number Generator  6 B- 20  is used in one embodiment for random transmission time determination associated with the common control channel transmission timing procedure. The ABS-MAC within Processor  6 B- 50  further interfaces to and from one or more Physical Layer entities/MODEMs including in-band embedded, in-band-inline, and out of band, common control channel. 
       FIG. 6C  is a flow diagram of the MAC receive process for an Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. During the MAC receive processing, the process begins, in the current embodiment, with Step  6 C- 10  waiting for the PHY to detect a first alert signature. 
     Once the first detection has occurred, the timing variables are set in Initialize step  6 C- 20 . In some embodiments, one or more of the variables may be set during initial system configuration as well. In the current embodiment, these variables include in the current embodiment, T Max   Alert , T Actual   Alert , T Min   Alert , T VALID   Alert . Next the MAC link processor waits for T Min   Alert , in Step  6 C- 30 , and then begins waiting for the next PHY indication of a subsequent valid detection in Step  6 C- 40 . If no symbol is detected within T VALID   Alert , (step  6 C- 50 ) then processing proceeds to step  6 C- 70  where the higher layer RLP is notified and reset. Such an occurrence may happen is signal is lost, of if the end of the current RLP frame is received. Alternatively, if an alert is detected for the specified peer MAC (as determined in the current embodiment by a property of the alert code set (SSj) such as a secondary orthogonal code for example), the appropriate timer values are adjusted and processing returns to step  6 C- 30  (the wait for T Min   Alert  step). In the current embodiment, various alerts may be received, and for each alert signature which is distinguishable from those from other ABS-MACs, a separate ABS-MAC receive process may be instantiated, along with individual timer values. 
       FIG. 6D  is a flow diagram of the MAC transmit process for a Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. The MAC transmit process begins in step  6 D- 10  where a MAC service data unit (SDU) is received. The SDU may be a single bit wherein the modulation is BPSK and the segmentation size is n=1. Alternatively, the segmentation size may be 2 bits, and the modulation may be QPSK. As is known by one or ordinary skill in the art, higher order modulations such as m-ary QAM, and discussed above may be used as well. Once a specific SDU is received by the MAC, permission to transmit may be requested for inline transmissions associated with step  6 D- 20 , so as to coordinate with the transmission of the IBR symbols in time. In step  6 D- 30  if the SDU indicates that a first SDU indication is present, a clear channel assessment (CCA) will be performed in some embodiments (for example when transmitting on the common control channel in one embodiment, though not limited to such an embodiments). In step  6 D- 50 , the timers are initialized, and processing proceeds to  6 D- 60 . Alternatively if there is not first SDU indication, in step  6 D- 30 , step  6 D- 40  is performed wherein the process waits for T VALID   ALERT  to be come valid, for example by comparing a timer or a clock value in different embodiments to the valid time frame T VALID   ALERT . 
     Processing then proceeds to step  6 D- 60  wherein the MAC waits for an indication from the RRC (in control of the fine scale timing in the current embodiment) to indicate authorization to transmit, if such authorization is required (associated with specific embodiments). Next, decision step  6 D- 70  directs processing based upon T VALID   ALERT  being valid. If expiration has occurred, an indication to the RLP is performed wherein a failure is signaled in step  6 D- 80 . Alternatively if T VALID   ALERT  remains valid, processing proceeds to step  6 D- 90  wherein the MAC PDU is transmitted. The format of the MAC PDU in some embodiments is a simple pass through to the PHY. In other embodiments a MAC header, or other information may be added to the MAC SDU prior to the MAC PDU being provided to the PHY. Finally, successful transmission is indicated to the RLP, and the process is exited in step  6 D- 100 . 
       FIG. 6E  is an illustration of the radio link protocol (RLP) message format of Advanced Backhaul Services control link control link according to one embodiment of the invention. As previously described in specific embodiments, the RLP receives a service data unit (SDU) from the ABS Packet Data Control Protocol (PDCP), including fields  6 E- 30  (Logical Channel) at least, and in some instances  6 E- 45  (the length of the remaining PDCP payload),  6 E- 50  (the destination address to which the packet is to be sent),  6 E- 60  (a variable length RRC message), and  6 E- 70  (a variable length user plane message from higher layers of an IBR for example. Other embodiments may also include the Sending MAC address  6 E- 20 . In other embodiments, the MAC address may be added within the RLP layer or another layer. 
     The RLP then next adds the Sync field  6 E- 10 , the CRC field  6 E- 40 , and performs FEC processing adding tail bits  6 E- 80 . The result is passed to the MAC as a RLP PDU/MAC SDU. 
       FIG. 7A  is a flow diagram of the RRC transmit process for a Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. When the RRC has information to transmit to a peer, or to broadcast alerts in general, the process begins in step  7 A- 10  wherein the ABS RRC receives a command from the Management Entity (ME) to transmit periodic alerts for example. In step  7 A- 20 , the RRC performs configuration of the various layers so as to transmit periodic alerts such as, in one example, setting the timer values, modulation formats, number of alert code sequences per alert signal transmission, RLP segmentation bits (n), and other associated parameters. In step  7 A- 30 , the RRC composes a message (PDU) for the PDCP layer and requests the transmission of an alert ( 7 A- 40 ). Next in the current exemplary embodiment, the RRC waits for T MIN   ALERT , and then returns to step  7 A- 40  to transmit another alert. 
       FIG. 7B  is a flow diagram of the RRC scan process for a Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. In the embodiment of  FIG. 7B , the ME requests the RRC perform a scan function (step  7 B- 10 ). The RRC then configures the appropriate layers using pre-determined information stored within the ABS system, or determined form received information form a registry for example in one embodiment. Other embodiments may receive information form the IBR or IBMS, or another source (step  7 B- 20 ). The specific parameters to be configured vary in different embodiments, but may include those described associated with step  7 A- 20  and elsewhere. In step  7 B- 30 , the RRC requests a scan from the ABS MAC for a specific duration TSCAN, and on a list of channels defined by CH SCAN . Finally, the RRC receives a report for each scan from the MAC, and once complete, reports the result to the ME in step  7 B- 40 . 
       FIG. 7C  is a flow diagram of the RRC Bloom process for an Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. The ABS RRC, in one embodiment, receives a request form the ME requesting the “Bloom” process (step  7 C- 10 ). Some embodiments the process includes entering the Bloom process register with the registry that it is entering the Bloom process. Other embodiments include the requirement, or option for the station performing the Bloom process to notify one or more stations which may receive interfering transmission of the state of entering the Bloom process, and optionally update such stations of that process. 
     Embodiments of the Bloom process include incrementally “progressive interference”, so as to initially have a lower impact in terms of interference to any existing ABS devices which happen to be with the propagation range of a new ABS device being brought up for operation. For example, a Tier 2 device being brought up in the vicinity of a Tier 1 Incumbent device with settings in the registry allowing for other devices to operate in the region but with limitations so as to not interfere with the T1-I device require, in one embodiment, a Bloom process. In fact, in some embodiments, any device having a lower tier, or same tier and having a lower priority or right to operate in the vicinity of other devices either as reported by a registry, or detected directly in some cases use a Bloom process. Such a process allows for the higher tier, or priority device (one having been operating in the area longer but of the same tier) an opportunity to detect interfering transmissions from a device performing a Bloom process. Such a process allows the level of interference to be detectable, but not necessarily catastrophic to the link of the existing devices. Step  7 C- 20  provides for the RRC to configure the Bloom process, defining in one embodiment a variable “Step” with a value of 0, initially. Additionally the other layers of the ABS stack are configured as well. Next, in step  7 C- 30 , the RRC initiates the ABS Bloom process utilizing parameters TXPower(n), and DutyCycle(n), where n is the step in the progressive Bloom process. After each step in the process, as the process returns to step  7 C- 30 , the setting will be retained for a period of time referred to as Dwell. The process stays in  7 C- 40  until the Dwell process for Step n has expired. In one embodiment, the transmit power will be the full Tx power expected for operation of the link, and the duty cycle as determined by DutyCycle(n) for each step n of the Bloom process, will be varied in increasing percentages of a pre-determined repetition time for the Dwell time, which may be varies as well on a per Bloom step process. In other embodiments, both the transmission power and the duty cycle will be varied progressively. In yet further embodiments, only the power will be varied, for a given duty cycle, or in any linear, or non-linear combination. In one embodiment of the Bloom process, only the basic alert signature is sent with no identifying information. In another embodiment, the alert signature is sent with a code unique, or another property unique to station in the Bloom process. In yet further embodiments, the Bloom process includes the identity of the transmitting station in the transmissions, and potentially additional information. 
     During the dwell process, prior to the expiration of the Dwell timer, or counter, the ABS station monitors communications channels (in various embodiments one or more of the common control channel, the inband control channel, or another out of band link) in step  7 C- 40  for any “direct messages” from another station notifying the Blooming ABS station of detected interference. Additionally, in step  7 C- 50  the Blooming ABS station checks the registry periodically for notification of detected interference due to the Bloom process. If either step receives an indication of detected interference, the process proceeds to step  7 C- 80  and the process (and the transmissions) are terminated in one embodiment. Note that in some embodiments, the process may be begun again, with adjusted transmission parameters so as to minimize interference to the station that detected the Bloom interference. In some embodiments, the indication of interference from another ABS station will include information usable to aid the Blooming station to avoid interfering with the detecting station with higher priority (either higher tier, or more seniority for example). Examples of the type of information usable to set interfere avoiding transmission settings were discussed previously in this disclosure associated with  FIGS. 4C, 4D, 4E, 4F, and 4G , and elsewhere. Additionally similar processing was discussed in co-pending application U.S. Ser. No. 13/371,346, the entirety of which is incorporated herein by reference. Note that based upon initial scans, prior to beginning the Bloom process, such interference avoiding techniques may be utilized based upon channel modeling and interference prediction techniques prior to beginning the transmission process in step  7 C- 30 , or configured in step  7 C- 20 . Such a step may also take input from any direct messages received related to detected interference or similar information receiving in the registry ( 4 C- 60 / 4 C- 70  for example) as a result of previous attempts at the Bloom process. 
     Returning now to step  7 C- 40 , once the Dwell time has expired, and no interference indication has been detected, the Bloom process Step is incremented in  7 C- 60 , and processing proceeds to step  7 C- 70 . If the Step is the Final Step, the process is terminated in  7 C- 80 , otherwise the process continues with new transmission settings in step  7 C- 30 . 
     Further details of the “bring up” of an ABS station, and the associated management of the Bloom process will be discussed associated with  FIG. 8C . 
       FIG. 8A  is an illustration of exemplary ABS registry entries according to one embodiment of the invention. Parameters associated with entries in the various embodiments of the registry  4 C- 60  are discussed in many locations in this disclose. 
     The table includes example registry entries for several different tiers of stations operating under the proposed ABS rules. The first column defines possible entries for one aspect of one embodiment of the registry. The FCC ID is typical of devices registered with the FCC, and is also required as noted with the white spaces rules. 
     The MAC Address is a 48-bit IEEE assigned address which can be used to identify a station from transmissions in one embodiment. 
     Lat, and Long provide the geographic latitude and longitude of the location of the ABS transmitter station. 
     In addition to Lat/Long, the Address may be entered as well and may be mandatory for a fixed station in some embodiments. 
     The Tier entry defines the class of service the ABS station is operating under as define in forgoing sections. 
     Tx Power defines the transmitter power of the ABS station. In some embodiments, it is the maximum allowable transmit power, while other embodiments include the actual transmitter power, or transmitter power the station is capable of transmitting. 
     Antenna Type indicates the type of antenna. For Tier 1 devices, this is more likely a fixed dish type antenna similar to entries for FCC Part 101 licenses. The Azimuth (Deg) and Elevation (m) relate to the antenna directivity and center pointing direction of a fixed antenna. Further examples include, but are not limited to azimuth beamwidth, elevation beamwidth (in degrees, not m), polarization, antenna height, azimuthal and elevation bearings at center of the pattern, etc. For devices of other tiers, or potentially for Tier 1 incumbent devices is some cases, the antenna type may further include whether the antenna is an antenna array, and any associated array attributes such as the array geometry (number of elements, and their relative geometric position), the number of receiver and/or transmitter elements, array capabilities such as receiver and transmitter null steering capacities, and the like. 
     Equipment ID is the FCC certification ID of the equipment being used and having been certified under ABS rules. 
     “Using Common Control Channel” is an entry for defining which common control channel, if any, a particular station is utilizing. 
     M-ACTUAL, M-TOT, M-REG, and Registered Channels(1 . . . M-REG) as discussed previously relate to the allowable and in use channels for operation under the ABS rules. 
     Duplexing Mode defines time division, frequency division, or so called zero division duplexing methods (or other such methods as may become applicable). 
     Licensed C/I (dB) is an entry of an embodiment in which the fees paid, and/or the license received (Tier 2 in one embodiment) defines a C/I for which the station receives interference protection assuming it is the highest tier, and has the seniority in that location. Further detail will be provided relating to “cooperative” interference mitigation and the Bloom process associated with the ME in  FIG. 8C . 
     The SIP Address entry is an example address in some tiered service radios by which a station may be contacted with a so-called direct message. For example, in a Blooming process when notification that the Blooming station is causing interference to another protected ABS device, a directed SIP message is sent to the Blooming station in one embodiment. 
     The P-MAX (dBm), P-NOM (dBm), P-Allow (dBm) are associated with the cooperative interference process for non-Tier 1 devices, and in one exemplary embodiment, are discussed in more detail elsewhere. 
     The Date Occupied (or optionally also Time Occupied) and Date Licensed fields are related to determining seniority between ABS stations of the same tier. The Geographic Region field defines the specific region in which a device is operating. Geographic regions were discussed in more detail relating to  FIG. 4D . 
       FIG. 8B  is a flow diagram of the Common Control Channel basic broadcast alert process for an Advanced Backhaul Services control link protocol processor according to one embodiment of the invention. In step  8 B- 10 , the ABS ME requests the ABS RRC broadcast a basic Alert. In step  8 B- 20  the ABS RRC requests the ABS_PDCP to transmit on logical channel (LC) 00, indicating a “basic alert”, which may also, in some embodiment be interpreted as an “end of packet”. In this embodiment, it is transmitted on common control channel 33. In other embodiments, the transmissions are transmitted in band as well, or in place of the common control channel transmissions. The process waits in step  8 B- 30  for the alert period to expire (T MIN   ALERT  in some embodiments). Once the period has expired, processing returns to step  8 B 0 - 20 , and continues. 
       FIG. 8C  is a flow diagram of the Management Entity (ME) Tier 2 channel selection and link initialization process for a Advanced Backhaul Services control link protocol processor according to one embodiment of the invention.  FIG. 8D  is a flow diagram of the Management Entity (ME) Tier 3 channel selection and link initialization process for a Advanced Backhaul Services control link protocol processor according to one embodiment of the invention.  FIG. 8D  is, in some embodiments, a very similar process to that of  FIG. 8C  and can be assumed to be the same, with exceptions as noted in the figure. 
     Referring now to Step  8 C- 10  the ME of the ABS device, checks the registry for any T1 (Tier 1) or T2 (Tier 2) devices in the local proximity for which in must consider interference and previous discussed. Of course for a Tier 3 device, other T3 devices are also checked in the registry as well (see step  8 D- 10 ). In step  8 C- 20  the ME determines channels not in T1 exclusion zones or currently used as T2 Channels. For T3 devices, other T3 devices must be considered as well. In step  8 C- 30  if no unused channels are available, step  8 C- 40  is performed, otherwise processing proceeds to step  8 C- 140 . In step  8 C- 140 , when clear channels are determined to be available, the ME configures the radio entities (layers), and registers the current configuration of the ABS station with the registry. The ME then begins broadcasting alerts, and notifies (in some embodiments) the IBR IBMS, which begins transmission to peer point to point radios or point to multipoint radios for payload traffic. The ME additionally begins to monitor the Registry and/or control channels for interference messages or any direct messages. 
     If no “clear” channels are available, step  8 C- 40  is performed and the ME determines from the Registry, which channels are candidates for use, so as to avoid or minimize interference to other T2 stations in the current embodiment. In step  8 C- 50 , the ME requests ABS RRC to perform a scan of candidate channels for operation so as to assess the interference potential of using these channels. Processing then proceeds to step  8 C- 60 , where the ME determines the best candidate channels for operation based upon scan results and registry information. Such a determination will, in some embodiments, involve propagation modeling and interference mitigation techniques as discussed. The Bloom process is then begun in step  8 C- 70 . ME begins “Bloom Process” and monitors the Registry and in-band and out-of-band channels for direct messages. The decision as to whether direct messages are received or not is performed in step  8 C- 90 . If no direct messages are received, the registry is checked for interference notifications in step  8 C- 130 . If no interference notification is received, the processing proceeds to step  8 C- 140  as previously discussed. Returning to step  8 C- 90 , if a direct message is received, step  8 C- 100  is performed where the ME will stop transmission and perform an interference mitigation process in one embodiment. Such an interference mitigation process, in some embodiments, includes responding to the “interfered with” station via direct message to negotiate cooperative interference mitigation interaction and measurements. Such mitigation may also include adjustments and “trial” test transmissions with iterative feedback from the partner “interference mitigation” station. If the interference is resolvable ( 8 C- 110 ) the processing proceeds to  8 C- 80  where the radio is configured with the determined radio parameters to avoid interference, and operation returns to  8 C- 90 . 
     If the interference is not resolvable in step  8 C- 110 , processing proceeds to step  8 C- 120  and transmission is halted and alternative channels are selected, and the process is restarted at step  8 C- 60 . 
     The “Bloom process” as discussed allows for progressive interference without initially being catastrophic to the station being interfered. In one embodiment, the process is a time division process wherein less than 100% transmit duty cycle is employed. For example, the Blooming ABS station may start at 10% and proceed to 20% and so on in the current embodiment. This is less damaging, and should not “shut off” the victim station. In one embodiment, if at any point the Blooming station receives a direct message indicating unacceptable interference, then the lower tier or lower priority Blooming ABS station has to cease and desist if requested to do so. The stations performing the Bloom process must be certified, as do the stations indicating they are being interfered to allow for the transmission of messages ordering another station to vacate certain channels. 
     In one embodiment, using the Registry, the registry control and arbitration processes between stations serves to order interfering stations to vacate certain channels. The registry time stamps registration so as to document the specific chronology of the ABS stations in a geographic area and can determine “priority” for same tier devices so as to arbitrate disputes and enforce rules. A station may send an “interference notification” message when interfered with, which is valid only if that station has been in the location earlier than the blooming stations. To ensure this process is legitimate, the Registry, as mentioned, can act as a policy arbitrator and enforcer based on the time of registration of the individual stations, or as a general process following procedural rules and steps. In some embodiments, there may be a requirement to accommodate others reasonably and work with them via the “cooperative interference mitigation process”. Such a requirement may be conditional based on the tiers of the stations, or the density of the stations within the area. For example, if one station can accommodate another station without affecting the performance of their link, they may be required to do so, or report that they cannot make adjustments. In some embodiments, the Registry may provide a benefit to that station in making accommodations for other stations in terms allowing more capability or an increase in the priority registration, for example. 
     In one embodiment the station notifying another station of harmful interference has the obligation to inform the interfering station of the level of interference and potentially other helpful information so as to aid in the reduction of interference and to verify that the interfering station is the correct one or that the message is not fraudulent, for example. Such an indication may be considered a “hint” as to how much of a change needs to be made, or if resolution is possible at all. Such information may include the frequencies the interference is occurring on, and the level of the interference as two examples. Other embodiments may include the channel state information or angle of arrival of the interfering signal. 
     In another embodiment, where an interfering station is being evicted from the currently Blooming or operating frequencies, the station must be given a interference mitigation time to resolve the interference in terms of adjustment of RF parameters as discussed. In one embodiment, a “notice message” or interference notification includes the specific overlapping channels, and by the specific amount of power. The mitigation may be considered a “cure time” from the first notice. Upon a second notice the station, in one embodiment, turns off transmissions immediately, unless a cooperative interference mitigation process is deemed to be ongoing. 
     An example of such a cooperative interference mitigation process follows: 
     1) When an ABS station detects another is interfering, it may invoke the eviction process. 
     2) The “interfering” station has 1 second to “cure” and must be informed by how much the interference must be reduced. 
     3) If direct messaging is implemented, one set of rules apply, if a “mail box” approach using the Registry is performed a second set of rules are utilized, which are less interactive and cooperative (in the current embodiment). Such a process is designed to “align interests”. 
     4) If there is a direct message, and notice, but not response from the interfering station, they are required to immediately terminate transmissions (which may be based upon the registry mail box notification process). 
     5) If there is notice to an interfering station via a direct message, and the interfering station responds, then that station will get an opportunity to fix the interference by adjusting RF parameters. For example, if a station wants to have the opportunity to stay and attempt to adapt, it must send a response to the registry in one embodiment, or directly to the notifying station (in the current embodiment). 
     6) If a notified ABS station estimates that it can cure the interference problem, and makes adjustment but does not respond to the notifying station, then if such adjustment has resolved the issue, no termination occurs as the secondary notice will not occur. 
     7) However, if a notified station does not respond, and attempts to fix the issue unsuccessfully, and receives a secondary interference notification it must cease transmission immediately in the current embodiment. 
     8) If a station does respond to the first direct interference notification, that station will receive multiple opportunities to resolve the interference cooperatively. 
     In some embodiments, the registry may need be to monitored and document the process so as to allow for review at a later time, allowing for an appeal process with a supervisory authority such as the FCC. If the rules are not followed, the registry may indicate directives to the stations up to and including revoking licenses, or adjusting “occupied” priority status. 
     In one embodiment, when a dedicated “Bloom” signal is detected (for example with a unique signature and no user payload), the detecting ABS station may look in the registry to determine which other stations are in the area and in the Bloom process so as to either determine identity or confirm identity. Such an embodiment requires that the “state” of a station be updated within the Registry. 
     In some embodiments, the “interfered with” ABS station judges an interference threshold based upon one or more of: BER impact, C/I impact, the power density of the interferer. 
     In one embodiment, licenses are paid for by station owners based upon the licensed “Carrier to Interference ratio” (C/I) that is desired or required at that location. Having licensed a specific C/I, and when interference impinges upon them damaging the C/I beyond the level of their license, there are several embodiments operable to resolve the problem. First, and most simply, the forgoing notification procedures may be followed. Secondly, in another related embodiment, a registered station gets a fixed amount of protection, and based upon the interference level being received, the licensed ABS station is allowed to increase its transmitter power by the amount of licensed C/I degradation that are currently receiving. For example, if you purchase a license, for 40 dB C/I, you are guaranteed 40 dBi or the maximum your equipment can do, up to the permissible transmission power limit in the band. In such an embodiment, a licensed station only transmits as much power as required for the target receiver to achieve the maximum C/I it can operate at, above the noise floor plus a nominal margin amount in some embodiments. Notification may only be provided, in the current embodiment, once a licensed station reaches a “conditional maximum”. The conditional maximum is the lower of the amount that that you are interfering with someone else, or all you can transmit. 
     In related embodiments, the C/I protection affects the license cost. For example, it might cost $1K for a 20 dB T2 license, or $2K for 25 dB T2 protection license, and so forth. 
     In one embodiment, the allowable transmit power follows the equation: 
         P   Allow =min( P   MAX   ,P   INFERENCE   ,P   R,C/I )  EQ. 8-1
 
     For example, if interference encroaches within the C/I you have purchased, the licensed station may increase its power to regain the licensed C/I. If the licensed ABS station has increased its power up to either P MAX  or P INTERFERENCE , then the offending (interfering) station may be notified to cease, or to follow the interference mitigation process described previously in various embodiments. 
     In one embodiment, if the owner of a device wants 45 dB C/I, then they need to pay more money to get cleaner spectrum. Associated with such rules they may be an occupancy requirement to retain the rights, as well as a requirement that no license may exceed the certified capability of C/I performance of the equipment being utilized for a given license. In one embodiment, one cannot purchase more protection than one&#39;s equipment can actually use. In another embodiment, the “notification” message must include, and the equipment generating the message must be able to measure the interference level at a C/I level and accuracy to which the notification indicates. 
     In a related embodiment, any device owner may purchase what every C/I level they want, but if the device cannot measure a specific C/I with sufficient accuracy, then it is not within the rules to notify an interferer of a level of C/I and as a result such a C/I is not enforceable by that equipment. Such equipment must, in specific embodiments, be certified that it can perform the specific measurements. 
     In one embodiment, the interference notification message is limited to a fixed interference back off step, such as 5 dB. If such a back off by the offending station does not cure the interference problem, another message may be sent. 
     One or more of the methodologies or functions described herein may be embodied in a computer-readable medium on which is stored one or more sets of instructions (e.g., software). The software may reside, completely or at least partially, within memory and/or within a processor during execution thereof. The software may further be transmitted or received over a network. 
     The term “computer-readable medium” should be taken to include a single medium or multiple media that store the one or more sets of instructions. The term “computer-readable medium” shall also be taken to include any medium that is capable of storing, encoding or carrying a set of instructions for execution by a machine and that cause a machine to perform any one or more of the methodologies of the present invention. The term “computer-readable medium” shall accordingly be taken to include, but not be limited to, solid-state memories, and optical and magnetic media. 
     Embodiments of the invention have been described through functional modules at times, which are defined by executable instructions recorded on computer readable media which cause a computer, microprocessors or chipsets to perform method steps when executed. The modules have been segregated by function for the sake of clarity. However, it should be understood that the modules need not correspond to discreet blocks of code and the described functions can be carried out by the execution of various code portions stored on various media and executed at various times. 
     It should be understood that processes and techniques described herein are not inherently related to any particular apparatus and may be implemented by any suitable combination of components. Further, various types of general purpose devices may be used in accordance with the teachings described herein. It may also prove advantageous to construct specialized apparatus to perform the method steps described herein. The invention has been described in relation to particular examples, which are intended in all respects to be illustrative rather than restrictive. Those skilled in the art will appreciate that many different combinations of hardware, software, and firmware will be suitable for practicing the present invention. Various aspects and/or components of the described embodiments may be used singly or in any combination. It is intended that the specification and examples be considered as exemplary only, with a true scope and spirit of the invention being indicated by the claims.