Patent Publication Number: US-8970326-B2

Title: Coaxial resonator and dielectric filter formed from a dielectric block with at least one inner conductor surrounded by a non-conductive recess

Description:
CROSS-REFERENCE TO THE RELATED APPLICATIONS 
     This application is a national stage of international application No. PCT/JP2010/066883, filed on Sep. 29, 2010 and claims the benefit of priority under 35 USC 119 to Japanese Patent Application No. 2009-247300, filed on Oct. 28, 2009 and Japanese Patent Application No. 2010-012652, filed on Jan. 23, 2010, the entire contents of all of which are incorporated herein by reference. 
     TECHNICAL FIELD 
     The present invention relates to a coaxial resonator having excellent electrical characteristics, and a dielectric filter, a wireless communication module and a wireless communication device including the coaxial resonator. 
     BACKGROUND ART 
     As a resonator for effecting resonance at a predetermined frequency, there has been known a coaxial resonator composed of a dielectric block, an inner conductor disposed in an inner surface of a through hole formed in the dielectric block, and an outer conductor disposed externally of the dielectric block (refer to Patent literature 1, for example). 
     CITATION LIST 
     Patent literature 
     
         
         Patent literature 1: Japanese Unexamined Patent Publication JP-A 1-227501 (1989) 
       
    
     SUMMARY OF THE INVENTION 
     Technical Problem 
     However, there has been a problem in the conventional-type coaxial resonator as proposed in Patent literature 1 in that the increasing of a Q value in the first resonant mode and the widening of the resonance frequency gap between the first resonant mode and the second resonant mode are difficult to achieve concurrently. Note that the first resonant mode refers to, among many existing resonant modes of the coaxial resonator, a resonant mode of the lowest resonance frequency, whereas the second resonant mode refers to a resonant mode of the second lowest resonance frequency. In general, the first resonant mode of coaxial resonators is used, and therefore the increasing of a Q value in the first resonant mode involves the improvement in the electrical characteristics of the coaxial resonator. Furthermore, the second resonant mode, becoming a spurious component, should desirably be apart in frequency from the first resonant mode. 
     The invention has been devised in view of the problem associated with the conventional art as mentioned supra, and accordingly an object of the invention is to provide a coaxial resonator having a high Q value in the first resonant mode and a wide resonance frequency gap between the first resonant mode and the second resonant mode, as well as to provide a dielectric filter, a wireless communication module, and a wireless communication device employing the same. 
     Solution to the Problem 
     A first coaxial resonator pursuant to the invention includes: a dielectric block; a first inner conductor disposed in an inner surface of a first through hole which extends from a first main surface of the dielectric block to an opposite second main surface thereof, the first inner conductor being connected to a reference potential at a side thereof toward the first main surface or at a side toward thereof the second main surface; and an outer conductor disposed over side surfaces of the dielectric block, the outer conductor surrounding the first inner conductor, the outer conductor being connected to the reference potential, wherein there is a low-dielectric-constant portion in a location between the first inner conductor and the outer conductor, and the low-dielectric-constant portion surrounds a periphery of the first inner conductor, and the low-dielectric-constant portion is lower in dielectric constant than the dielectric block. 
     Moreover, according to a second coaxial resonator pursuant to the invention, in the first coaxial resonator, the low-dielectric-constant portion is a recess which is disposed in the first main surface of the dielectric block. 
     Further, according to a third coaxial resonator pursuant to the invention, in the second coaxial resonator, the first inner conductor is connected to the reference potential at the side thereof toward the first main surface. 
     A dielectric filter pursuant to the invention includes: a plurality of any one of the first to third coaxial resonators, the plurality of the coaxial resonators comprising a plurality of the first through holes which comprise the first inner conductor in the respective inner surfaces and are arranged in a row in the dielectric block at distances; a second through hole being adjacent to one of the first through holes, the one of the first through holes being located at one end of the row, the second through hole extending from the first main surface to the second main surface of the dielectric block, the second through hole comprising a second inner conductor which is disposed in an inner surface of the second through hole and is electrically connected to an external circuit; and a third through hole being adjacent to another of the first through holes, the another of the first through holes being located at another end of the row, the third through hole extending from the first main surface to the second main surface of the dielectric block, the third through hole comprising a third inner conductor which is disposed in an inner surface of the third through hole and is electrically connected to an external circuit, wherein there is the low-dielectric-constant portion in a location between the first inner conductors and the outer conductor, and the low-dielectric-constant portion surrounds the periphery of each of the first inner conductors. 
     A wireless communication module pursuant to the invention includes: an RF section including the dielectric filter; and a baseband section connected to the RF section. 
     A wireless communication device pursuant to the invention includes: the wireless communication module; and an antenna connected to the RF section of the wireless communication module. 
     Advantages Effects of Invention 
     According to the coaxial resonator of the invention, it is possible to obtain a coaxial resonator having a high Q value in the first resonant mode and a wide resonance frequency gap between the first resonant mode and the second resonant mode. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         FIG. 1  is an external perspective view schematically showing a coaxial resonator in accordance with a first embodiment of the invention; 
         FIG. 2  is a sectional view of the coaxial resonator taken along the line A-A′ shown in  FIG. 1 ; 
         FIG. 3  is a plan view schematically showing a first main surface of a dielectric filter in accordance with a second embodiment of the invention; 
         FIG. 4  is a plan view schematically showing a second main surface of the dielectric filter shown in  FIG. 3 ; 
         FIG. 5  is a sectional view of the dielectric filter taken along the line B-B′ shown in  FIG. 3 ; and 
         FIG. 6  is a block diagram schematically showing a wireless communication module and a wireless communication device in accordance with a third embodiment of the invention. 
     
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     Hereinafter, a coaxial resonator pursuant to the invention will be described in detail with reference to the accompanying drawings. 
     First Embodiment 
       FIG. 1  is an external perspective view schematically showing a coaxial resonator in accordance with a first embodiment of the invention.  FIG. 2  is a sectional view of the coaxial resonator taken along the line A-A′ shown in  FIG. 1 . 
     As shown in  FIGS. 1 and 2 , the coaxial resonator of the embodiment includes a dielectric block  10 , a through hole  11 , a first inner conductor  13 , an outer conductor  15 , a recess  17 , and a grounding conductor  19 . The dielectric block  10  is formed of a rectangular parallelepiped dielectric body. The through hole  11  passes through the dielectric block  10  from a central part of a first main surface of the dielectric block  10  to a central part of an opposite second main surface thereof. The recess  17  is disposed between the outer edge of the first main surface of the dielectric block  10  and the through hole  11 , at a distance to both of them, in the shape of a rectangular loop surrounding the periphery of the through hole  11 . Moreover, no conductor is disposed in the inner surface of the recess  17 , and therefore the inner surface of the recess  17  constitutes a conductor-free region. Further, since the interior of the recess  17  is filled with air, it follows that a dielectric constant of the interior of the recess  17  is lower than a dielectric constant of an area of the dielectric block  10  exclusive of the recess  17 . That is, the interior of the recess  17  constitutes a low-dielectric-constant portion which is lower in dielectric constant than its neighboring dielectric block  10 . 
     The grounding conductor  19  is disposed over the entire area of the first main surface of the dielectric block  10  exclusive of the recess  17 , and is connected to a reference potential (ground potential). The outer conductor  15  extends throughout all of the four side surfaces of the dielectric block  10  while surrounding the first inner conductor  13 . Moreover, the outer conductor  15  is connected to the grounding conductor  19  located outwardly of the recess  17  of one of the main surfaces of the dielectric block  10 . Through the grounding conductor  19 , the outer conductor  15  is connected to the reference potential (ground potential). The first inner conductor  13  lies over the entire area of the inner surface of the through hole  11 . Moreover, one end of the first inner conductor  13  in its lengthwise direction is connected to the grounding conductor  19  located between the through hole  11  and the recess  17  at the first main surface of the dielectric block  10 . Through the grounding conductor  19 , the one end of the first inner conductor  13  is connected to the reference potential (ground potential). Note that the second main surface of the dielectric block  10  is designed as an open end without the placement of a conductor. 
     According to the coaxial resonator of the embodiment thusly constructed, there are provided the first inner conductor  13  and the outer conductor  15  surrounding the first inner conductor  13  at a distance, with the dielectric body lying in between. Therefore, for example, when one end of the first inner conductor  13 , as well as the outer conductor  15 , is connected to the reference potential (ground potential) through the grounding conductor  19 , the coaxial resonator functions as a coaxial resonator for effecting resonance at a predetermined frequency. 
     Moreover, in the coaxial resonator of the embodiment, the first main surface of the dielectric block  10  is provided with the recess  17  which surrounds the periphery of the first inner conductor  13  in a location between the first inner conductor  13  and the outer conductor  15 . Further, no conductor is disposed in the inner surface of the recess  17 , and therefore the inner surface of the recess  17  constitutes a conductor-free region. In addition, the recess  17 , being filled with air, serves as a low-dielectric-constant portion which is lower in dielectric constant than its neighboring dielectric block  10 . In this construction, an electric field produced between the first inner conductor  13  and the outer conductor  15  is allowed to pass through the recess  17 . Moreover, since the dielectric constant of the interior of the recess  17  is lower than the dielectric constant of the dielectric block  10 , it is possible to decrease the effective dielectric constant of the region between the first inner conductor  13  and the outer conductor  15 . Accordingly, in contrast to a coaxial resonator which has the same resonance frequency of the first resonant mode but is devoid of the recess  17  serving as a low-dielectric-constant portion, in the coaxial resonator of the embodiment, although the first inner conductor  13  needs to be designed to have a somewhat longer length, a higher Q value can be obtained in the first resonant mode. Note that research and studies based on electromagnetic field analysis conducted by the inventors have shown that the first resonant mode as employed herein is of a mode in which an electric field is oriented radially in a direction from the first inner conductor toward the outer conductor. 
     Further, according to the coaxial resonator of the embodiment, since the recess  17  serving as a low-dielectric-constant portion surrounds the whole periphery of the first inner conductor  13  continuously, it is possible to achieve a reduction in effective dielectric constant omnidirectionally around the periphery of the first inner conductor  13 , and thereby widen the resonance frequency gap between the first resonant mode and the second resonant mode. That is, according to the result of electromagnetic field analysis-based research and studies conducted by the inventors, for example, in a case where the recess  17  is disposed at each of two locations that are opposed to each other, with the first inner conductor  13  portion existing on a straight line segment passing through the first inner conductor  13  lying in between, the second resonant mode is defined by a resonant mode in which an electric field is oriented perpendicular to the through hole  11  in a recess free region. After all, the advantageous effect of the recess  17  to widen the resonance frequency gap between the first resonant mode and the second resonant mode cannot be obtained at all. Furthermore, for example, in a case where an L-shaped recess  17  is disposed around the first inner conductor  13  in such a manner as to cover two sides of the first inner conductor  13  extending in different directions at a right angle as seen with respect to the first inner conductor  13 , the second resonant mode is defined by a resonant mode in which an electric field is oriented perpendicular to the through hole  11  in a recess free L-shaped region corresponding to the other two sides. After all, there is little advantageous effect of the recess  17  to widen the resonance frequency gap between the first resonant mode and the second resonant mode. By way of contrast, in the coaxial resonator of the embodiment, since the recess  17  surrounds the whole periphery of the first inner conductor  13  continuously, it is possible to achieve a reduction in effective dielectric constant omnidirectionally around the periphery of the first inner conductor  13 , and thereby widen the resonance frequency gap between the first resonant mode and the second resonant mode. 
     Still further, according to the coaxial resonator of this embodiment, since the first inner conductor  13  is connected to the ground potential at a side thereof toward the first main surface, it follows that the recess  17  serving as a low-dielectric-constant portion is situated around the grounded end of the first inner conductor  13 . In this way, in contrast to a case where a low-dielectric-constant portion is formed around the open end of the first inner conductor  13 , the resonance frequency gap between the first resonant mode and the second resonant mode can be widened even further. The reason why such an effect can be attained is probably because the effective dielectric constant of the region around the grounded end of the first inner conductor  13  becomes smaller than the effective dielectric constant of the region around the open end of the first inner conductor  13 , with the consequence that the impedance at the grounded end of the first inner conductor  13  becomes greater than the impedance at the open end of the first inner conductor  13 . 
     In order to obtain a remarkable advantageous effect, it is preferable that the depth dimension of the recess  17  is greater than or equal to one-half of the thickness dimension of the dielectric body between the first main surface and the second main surface of the dielectric block  10 . Moreover, the larger the width of the recess  17  becomes, the greater the intended effect becomes. However, if the recess  17  has an unduly large width, the mechanical strength thereof will be decreased. Accordingly, it is advisable to set the width of the recess  17  at an appropriate value with consideration given to the dielectric constant, size, and mechanical strength of the dielectric block  10  and the level of the intended effect. 
     Second Embodiment 
       FIG. 3  is a plan view schematically showing a first main surface of a dielectric filter in accordance with a second embodiment of the invention.  FIG. 4  is a plan view schematically showing a second main surface of the dielectric filter shown in  FIG. 3 .  FIG. 5  is a sectional view of the dielectric filter taken along the line B-B′ shown in  FIG. 3 . Note that the following description deals only with the points of difference from the preceding embodiment, and the constituent components of the second embodiment similar to those of the preceding embodiment will be identified with like reference symbols, and overlapping descriptions will be omitted. 
     As shown in  FIGS. 3 to 5 , the dielectric filter of the embodiment includes a dielectric block  10 , a plurality of first through holes  11   a  and  11   b , a second through hole  21 , a third through hole  31 , a recess  17  ( FIGS. 3 ,  5 ), a plurality of first inner conductors  13   a  and  13   b , a second inner conductor  23  ( FIG. 5 ), a third inner conductor  33  ( FIG. 5 ), an outer conductor  15 , a grounding conductor  19 , a first input-output electrode  41  ( FIGS. 3 ,  5 ), a second input-output electrode  42  ( FIGS. 3 ,  5 ), and first to fourth capacitance electrodes  51 ,  52 ,  53  and  54  ( FIGS. 4 ,  5 ). 
     The plurality of first through holes  11   a  and  11   b  are arranged in a row in the dielectric block at distances, and extend from a first main surface of the dielectric block to an opposite second main surface thereof. The first inner conductor  13   a  lies over the entire area of the inner surface of the first through hole  11   a , and likewise the first inner conductor  13   b  lies over the entire area of the inner surface of the first through hole  11   b . Moreover, the first inner conductor  13   a ,  13   b  is connected, at a side thereof toward the first main surface, to the grounding conductor  19  ( FIGS. 4 and 5 ). Through the grounding conductor  19 , the first inner conductors  13   a  and  13   b  are connected to the ground potential. 
     The recess  17  is disposed in the first main surface of the dielectric block  10  and surrounds the peripheries of the first inner conductors  13   a  and  13   b  continuously in a location between the first inner conductor  13   a ,  13   b  and the outer conductor  15 . The inner surface of the recess  17  constitutes a conductor-free region. 
     The second through hole  21  is adjacent to the first through hole  11   a  located at one end of the row, and extends from the first main surface to the second main surface of the dielectric block  10 . The second inner conductor  23  is disposed in the inner surface of the second through hole  21  while making connection with the first input-output electrode  41  disposed in the first main surface of the dielectric block  10 . Through the first input-output electrode  41 , the second inner conductor  23  is electrically connected to an external circuit. 
     The third through hole  31  is adjacent to the first through hole  11   b  located at the other end of the row, and extends from the first main surface to the second main surface of the dielectric block  10 . The third inner conductor  33  is disposed in the inner surface of the third through hole  31  while making connection with the second input-output electrode  42  disposed in the first main surface of the dielectric block  10 . Through the second input-output electrode  42 , the third inner conductor  33  is electrically connected to an external circuit. 
     The grounding conductor  19  is disposed in an area of the first main surface of the dielectric block  10  exclusive of the recess  17  so as to be spaced away from the first input-output electrode  41  and the second input-output electrode  42 , and is connected to the ground potential. The outer conductor  15  extends throughout all of the four side surfaces of the dielectric block  10  while surrounding the first inner conductors  13   a  and  13   b , and is connected to the grounding conductor  19 . Through the grounding conductor  19 , the outer conductor  15  is connected to the ground potential. 
     The first to fourth capacitance electrodes  51  to  54  are arranged side by side at the second main surface of the dielectric block  10 . A predetermined electrostatic capacitance is made between the adjacent capacitance electrodes. Moreover, the first capacitance electrode  51  is connected to the second inner conductor  23 , the second capacitance electrode  52  is connected to the first inner conductor  13   a , the third capacitance electrode  53  is connected to the first inner conductor  13   b , and the fourth capacitance electrode  54  is connected to the third inner conductor  33 . 
     In the dielectric filter of the embodiment thusly constructed, upon the input of an electric signal to the second inner conductor  23  via the first input-output electrode  41  connected to an external circuit, then the coaxial resonator composed of the first inner conductor  13   a  and the outer conductor  15  is excited mainly by a coupling based on electrostatic capacitance between the first capacitance electrode  51  and the second capacitance electrode  52 . Also, the coaxial resonator composed of the first inner conductor  13   b  and the outer conductor  15  is excited mainly by a coupling based on electrostatic capacitance between the second capacitance electrode  52  and the third capacitance electrode  53 . Then, mainly by a coupling based on electrostatic capacitance between the third capacitance electrode  53  and the fourth capacitance electrode  54 , the electric signal is outputted via the third inner conductor  33  and the second input-output electrode  42 . At this time, since signals that lie in a certain frequency band including the resonance frequency of the coaxial resonator are selectively passed, the dielectric filter functions as a bandpass filter. 
     Thus, the dielectric filter of this embodiment is constructed by forming the plurality of the coaxial resonators of the first embodiment as described previously in the dielectric block  10 . By electrically coupling these coaxial resonators to each other, a bandpass filter is implemented. 
     According to the dielectric filter of the embodiment thusly constructed, a bandpass filter is implemented with use of the coaxial resonators having a high Q value and a wide resonance frequency gap between the first resonant mode and the second resonant mode. Accordingly, it is possible to obtain a dielectric filter having low losses, a small spurious extent in the vicinity of pass band, and excellent frequency selectivity. 
     Moreover, according to the dielectric filter of the embodiment, the recesses  17  surrounding the peripheries of the plurality of first inner conductors  13   a  and  13   b , respectively, are integral in one piece, and therefore the first inner conductors  13   a  and  13   b  can be arranged adjacent each other without undesirable wasted space and deterioration in mechanical strength. 
     In the dielectric filter of the embodiment, and in the above-stated coaxial resonator of the first embodiment as well, as the material of construction of the dielectric block  10 , for example, a resin material such as epoxy resin or ceramics such as dielectric ceramics can be used. For example, a glass-ceramic material is desirable for use that is composed of a dielectric ceramic material such as BaTiO 3 , Pb 4 Fe 2 Nb 2 O 12 , or TiO 2 , and a glass material such as B 2 O 3 , SiO 2 , Al 2 O 3 , or ZnO, and can be fired at relatively low temperatures ranging from about 800° C. to 1200° C. As the material of construction of various electrodes and conductors for use, for example, an electrically conductive material composed predominantly of a Ag alloy such as Ag, Ag—Pd, or Ag—Pt, a Cu-based conductive material, a W-based conductive material, a Mo-based conductive material, a Pd-based conductive material, and so forth are desirable for use. The thickness of each of the electrodes and conductors is adjusted to fall in a range of 0.001 mm to 0.2 mm, for example. 
     Third Embodiment 
       FIG. 6  is a block diagram schematically showing a wireless communication module  80  and a wireless communication device  85  in accordance with a third embodiment of the invention. 
     The wireless communication module  80  of this embodiment includes a baseband section  81  configured to process baseband signals and an RF section  82  connected to the baseband section  81 , and configured to process RF signals obtained after modulation or before demodulation of baseband signals. The RF section  82  includes a dielectric filter (BPF)  821  based on the above-stated second embodiment. In the RF section  82 , out of RF signals resulting from modulation of baseband signals or received RF signals, those that lie outside the communication band are attenuated by the dielectric filter (BPF)  821 . 
     More specifically, in this construction, the baseband section  81  includes a baseband IC  811 , and the RF section  82  includes an RF IC  822  connected between the dielectric filter  821  and the baseband section  81 . Note that another circuit may be interposed between these circuits. With the connection of an antenna  84  to the dielectric filter  821  of the wireless communication module  80 , the construction of the wireless communication device  85  of the embodiment for transmission and reception of RF signals will be completed. 
     According to the wireless communication module  80  and the wireless communication device  85  of the embodiment thus constructed, since wave filtering is performed on communication signals with use of the dielectric filter  821  having lower loss and excellent frequency selectivity, it is possible to decrease attenuation and noise of communication signals, and thereby impart high-quality communication performance capability to the wireless communication module  80  and the wireless communication device  85 . 
     Modified Examples 
     It should be understood that the application of the invention is not limited to the specific embodiments described heretofore, and that various changes and modifications are possible without departing from the spirit and scope of the invention. Where the above-described first and second embodiments are concerned, although there is described a case where the recess  17  having the shape of a rectangular frame is formed, the invention is not limited thereto. It is sufficient only that the recess  17  is disposed between the inner conductor and the outer conductor and surrounds the inner conductor at a distance. For example, the recess  17  may be given the shape of a polygonal frame instead of the rectangular frame, or may be annular-shaped. Also, the recess  17  may be given a shape like the letter “C” so that it surrounds two-thirds or more of the periphery of the inner conductor rather than having the shape of a continuous ring. Moreover, it is possible to arrange a plurality of recesses  17  at predetermined spacing and surround the periphery of the inner conductor. In this case, if the adjacent recesses  17  are situated at widely spaced points, the effectiveness of the recesses will be reduced. Therefore, it is desirable to minimize the spacing between the adjacent recesses  17 . 
     Moreover, where the above-described first and second embodiments are concerned, although there is described a case where the recess  17  whose interior is filled with air constitutes a low-dielectric-constant portion, the invention is not limited thereto. For example, the interior of the recess  17  may be filled with a dielectric material which is smaller in dielectric constant than its neighboring dielectric block. Also, the low-dielectric-constant portion may be made of a space disposed inside the dielectric block instead of the recess  17  disposed in the surface of the dielectric block. In this case, a vacuum may be created in the space, or alternatively the space may be filled with a dielectric material which is lower in dielectric constant than its neighboring dielectric block (including air). 
     Moreover, where the above-described dielectric filter of the second embodiment is concerned, there is described a case where a single recess  17  in one-piece form surrounds the plurality of first inner conductors  13   a  and  13   b . However, the plurality of recesses  17  may surround the plurality of first inner conductors, respectively. 
     Further, where the above-described first and second embodiments are concerned, there is described a case where the first inner conductor  13  and the outer conductor  15  are connected to the ground potential at the side of the first main surface of the dielectric block  10  formed with the recess  17 . However, the first inner conductor  13  and the outer conductor  15  may be connected to the ground potential at the side of the second main surface of the dielectric block  10 . 
     Still further, where the above-described dielectric filter of the second embodiment is concerned, there is described a case where there are provided two coaxial resonators composed of two first inner conductors  13   a  and  13   b  arranged in two first through holes  11   a  and  11   b , respectively, of the dielectric block  10  and the outer conductor  15 . However, the invention is not limited thereto. It is therefore possible to provide three or more coaxial resonators. In general, the resonators are provided in a total number not exceeding about 20, because an increase in the number of resonators leads to apparatus upsizing. 
     EXAMPLES 
     Next, concrete examples of the coaxial resonator pursuant to the invention will be described. 
     The electrical characteristics of the coaxial resonator implemented by way of the first embodiment of the invention as shown in  FIGS. 1 and 2  were calculated by a simulation in accordance with the finite element method. A frequency gap between the resonance frequency of the first resonant mode and the resonance frequency of the second resonant mode and an unloaded Q in the first resonant mode were selected as target electrical characteristics to be determined by calculation. 
     The conditions set for the coaxial resonator subjected to this simulation were: the dielectric body constituting the dielectric block  10  had a relative permittivity of 15 and a dielectric loss tangent of 0.0001; the conductors in use were made of copper; the dielectric block  10  had the form of a rectangular parallelepiped which was 16 mm in length and width, and was 12.5 mm in the distance from the first main surface to the second main surface thereof; the through hole  11  had a diameter of 4.444 mm; the recess  17  had a width of 1.778 mm and surrounded the through hole  11  at a center of the region between the outer edge of the first main surface, as well as the second main surface, and the through hole  11 ; and the interior of the recess bore air. In order to obtain a simulation model, this coaxial resonator was placed in a rectangular parallelepiped cavity surrounded by a conductor, with its first main surface and four side surfaces kept in contact with the inner wall of the cavity, and with its second main surface opposed to the inner wall at a distance of 5 mm. 
     At this time, in the first resonant mode, a resonance frequency of 1.95 GHz and a Q value of 2382 were observed. Moreover, in the second resonant mode, a resonance frequency of 4.47 GHz was observed. That is, the resonance frequency gap between the first resonant mode and the second resonant mode was found to be 2.52 GHz. 
     On the other hand, in a coaxial resonator devoid of the recess  17  implemented by way of a comparative example, under the condition that the distance from the first main surface to the second main surface is 9.6 mm, although the resonance frequency of the first resonant mode was 1.96 GHz which is nearly equal to that of the coaxial resonator of the invention, the Q value of the first resonant mode was 2098. This value was smaller by more than 10% from that of the coaxial resonator of the invention. Furthermore, the resonance frequency of the second resonant mode was 3.63 GHz. That is, the resonance frequency gap between the first resonant mode and the second resonant mode was found to be 1.67 GHz. This value is smaller by more than 30% from that of the coaxial resonator of the invention. It will thus be seen that the invention has proven itself. 
     REFERENCE SIGNS LIST 
     
         
         
           
               10 : Dielectric block 
               11 ,  11   a ,  11   b : First through hole 
               13 ,  13   a ,  13   b : First inner conductor 
               15 : Outer conductor 
               17 : Recess 
               21 : Second through hole 
               23 : Second inner conductor 
               31 : Third through hole 
               33 : Third inner conductor 
               80 : Wireless communication module 
               81 : Baseband section 
               82 : RF section 
               821 : Dielectric filter 
               84 : Antenna 
               85 : Wireless communication device