Patent Publication Number: US-6985023-B2

Title: Selective switching of a transistor&#39;s back gate potential

Description:
CROSS-REFERENCE TO RELATED APPLICATIONS 
   This application is based upon and claims the benefit of priority from the prior Japanese Patent Application No. 2003-023324, filed Jan. 31, 2003, the entire contents of which are incorporated herein by reference. 
   BACKGROUND OF THE INVENTION 
   1. Field of the Invention 
   The present invention relates to a semiconductor device, and in particular, to a semiconductor device having a P-channel transistor to which a well voltage is applied. 
   2. Description of the Related Art 
   In semiconductor memory devices, a control circuit controlling memory cells is formed around the memory cells. The control circuit comprises elements such as a transistor or diode. For example, the control circuit is composed of a P-channel transistor  40  shown in FIG.  5 . The P-channel transistor  40  is formed in a substrate or well formed in the substrate, and supplied with well voltage (back gate voltage) VB in addition to gate voltage VG, source voltage VS and drain voltage VD. The Source voltage VS is supplied from a first power supply and it is a power supply potential Vcc. The Well voltage VB is supplied from a second power supply formed of a charge-pump circuit in the semiconductor memory device, and it is usually a boosted potential Vpp. That is, VB=Vpp≧VS=Vcc. 
   As illustrated in  FIG. 6 , the P-channel transistor  40  comprises first semiconductor region  51 , P-type second semiconductor regions  52 ,  53 , and gate electrode  54 . The first semiconductor region  51  is formed of an N-type well or N-type semiconductor substrate. The P-type second semiconductor regions  52  and  53  are formed in the first semiconductor region  51 , and constitute source and drain regions of the P-channel transistor  40 . The gate electrode  54  is formed on the first semiconductor region  51  via a gate insulating film. The gate electrode  54 , second semiconductor regions  52 ,  53  and first semiconductor regions  51  are supplied with gate voltage VG, source voltage VS, drain voltage VD and well voltage VB, respectively. 
   JPN. PAT. APPLN. KOKAI Publication No. 7-131332 is given as the document relevant to a CMOS circuit having the following structure. According to the structure, P-channel and N-channel MOS transistors are connected in series, and the node between both MOS transistors is used as an output terminal. In  FIG. 1  of the foregoing publication, there is shown a circuit, which blocks a reverse current from the output side so that undesired current cannot be carried. 
   FIG.  5  and  FIG. 6  are a circuit diagram and cross-sectional view showing a conventional semi-conductor device. In a P-channel transistor  40 , well voltage VB is usually set to a voltage higher than source voltage VS. However, if many cells are operated and a large current flows through a power supply supplying boosted potential Vpp, the boosted potential falls; for this reason, the well voltage VB becomes lower than the source voltage VS. In addition, when noise is generated, the boosted potential falls; for this reason, the well voltage VB becomes lower than the source voltage VS. When the potential of the boosted potential falls and the well voltage VB becomes lower than the source voltage VS by the threshold value of the PN junction between source and well, the PN junction between source and well is forward-biased; therefore, it turns on. As seen from the arrows shown in  FIG. 6 , a large numbers of carriers are generated in a substrate. For this reason, there is a problem that a parasitic transistor comprising substrate, source and well latches up, and large current flows therethrough. 
   BRIEF SUMMARY OF THE INVENTION 
   According to an aspect of the present invention, there is provided a semiconductor device comprising: 
   a first transistor having a first conduction type first semiconductor region and a second conduction type second semiconductor region formed in the first semi-conductor region, the first semiconductor region being supplied with a first prescribed potential, the second semiconductor region being supplied with a second prescribed potential; and 
   a potential generator circuit generating the first prescribed potential, wherein 
   the potential generator circuit has a first power supply terminal supplied with a first power supply potential, a second power supply terminal supplied with a second power supply potential set to a higher potential than the first power supply potential, and an output terminal outputting the first prescribed potential, and 
   the potential generator circuit outputs the second power supply potential as the first prescribed potential when the second power supply potential is higher than a predetermined potential, and outputs the first power supply potential as the first prescribed potential when the second power supply potential is lower than the predetermined potential. 
   According to another aspect of the present invention, there is provided a semiconductor device comprising: 
   a first transistor having a first conduction type first semiconductor region and a second conduction type second semiconductor region formed in the first semiconductor region, the first semiconductor region being supplied with a first prescribed potential, the second semiconductor region being supplied with a second prescribed potential; and 
   a potential generator circuit generating the first prescribed potential, wherein 
   the potential generator circuit has a first power supply terminal supplied with a first power supply potential, a second power supply terminal supplied with a second power supply potential set to a higher potential than the first power supply potential, and an output terminal outputting the first prescribed potential, and 
   the potential generator circuit comprises: 
   a second transistor having a source connected to the second power supply terminal supplied with the second power supply potential, and a drain connected to the output terminal outputting the first prescribed potential; 
   a third transistor having source and gate connected to the first power supply terminal supplied with the first power supply potential, and a drain connected to the output terminal outputting the first prescribed potential; and 
   an inverter circuit having an input terminal connected to the second power supply terminal, and an output terminal connected to the gate of the second transistor. 
   According to a further aspect of the present invention, there is provided a semiconductor device comprising: 
   a first transistor having a first conduction type first semiconductor region and a second conduction type second semiconductor region formed in the first semiconductor region, the first semiconductor region being supplied with a first prescribed potential, the second semiconductor region being supplied with a second prescribed potential; and 
   a potential generator circuit generating the first prescribed potential, wherein 
   the potential generator circuit has a first power supply terminal supplied with a first power supply potential, a second power supply terminal supplied with a second power supply potential set to a higher potential than the first power supply potential, and an output terminal outputting the first prescribed potential, and 
   the potential generator circuit comprises: 
   a second transistor having a source connected to the second power supply terminal supplied with the second power supply potential, and a drain connected to the output terminal outputting the first prescribed potential; 
   a third transistor having source and gate connected to the first power supply terminal supplied with the first power supply potential, and a drain connected to the output terminal outputting the first prescribed potential; and 
   a comparator circuit including a differential amplifier circuit having a pair of input terminals and an output terminal; 
   wherein one of the pair of input terminals of the differential amplifier circuit of the comparator circuit is connected with the first power supply terminal, the other thereof is connected with a source of a fourth transistor having drain and gate both connected to the first power supply terminal, and the output terminal of the differential amplifier circuit of the comparator circuit is connected to the gate of the second transistor. 

   
     BRIEF DESCRIPTION OF THE SEVERAL VIEWS OF THE DRAWING 
       FIG. 1  is a circuit diagram showing a semiconductor device; 
       FIG. 2  is a cross-sectional view showing the semiconductor device of  FIG. 1 ; 
       FIG. 3  is a circuit diagram showing a semiconductor device according to a first embodiment of the present invention; 
       FIG. 4  is a circuit diagram showing a semiconductor device according to a second embodiment of the present invention; 
       FIG. 5  is a circuit diagram and showing a conventional semiconductor device; and 
       FIG. 6  is a cross-sectional view showing the conventional semiconductor device of FIG.  5 . 
   

   DETAILED DESCRIPTION OF THE INVENTION 
   Embodiments of the present invention will be described below with reference to the accompanying drawings. 
   (First Embodiment) 
   A semiconductor device according to a first embodiment of the present invention will be explained below with reference to  FIG. 1  to FIG.  3 . 
     FIG. 1  is a circuit diagram showing a semi-conductor device,  FIG. 2  is a cross-sectional view showing the semiconductor device of  FIG. 1 , and  FIG. 3  is a circuit diagram showing a semiconductor device according to the first embodiment of the present invention. 
   In semiconductor memory devices, a control circuit controlling memory cells is formed around the memory cells. The control circuit comprises elements such as a transistor or diode. For example, the control circuit is composed of a P-channel transistor  10  shown in FIG.  1 . The P-channel transistor  10  is formed in a substrate or well formed in the substrate, and supplied with well voltage (back gate voltage) VB in addition to gate voltage VG, source voltage VS and drain voltage VD. The voltage VB is not limited to the well voltage, and a substrate voltage may be supplied. 
   As illustrated in  FIG. 2 , the P-channel transistor  10  comprises first semiconductor region  11 , P-type second semiconductor regions  12 ,  13 , and gate electrode  14 . The first semiconductor region  11  is formed of an N-type well or N-type semiconductor substrate. The P-type second semiconductor regions  12  and  13  are formed in the first semiconductor region  11 , and constitute source and drain regions of the P-channel transistor  10 . The gate electrode  14  is formed on the first semiconductor region  11  via a gate insulating film. The gate electrode  14 , second semiconductor regions  12 ,  13  and first semiconductor regions  11  are supplied with gate voltage VG, source voltage VS, drain voltage VD and well voltage VB, respectively. 
   Controlled boosted potential Vpp′ is supplied as the well voltage VB of the P-channel transistor  10 . A well voltage generator circuit shown in  FIG. 3  generates the controlled boosted potential Vpp′. The well voltage generator circuit is provided with terminals A and B. The terminal A receives boosted potential Vpp supplied from a second power supply comprising a charge pump circuit (not shown) in the semiconductor memory device. On the other hand, the terminal B receives power supply potential Vcc supplied from a first power supply. The controlled boosted potential Vpp′ is outputted from an output terminal. A potential switching circuit  20  is interposed between the terminals A and B. The potential switching circuit  20  has the configuration in which a P-channel transistor  21  and an N-channel transistor  22  are connected in series between the terminals A and B. The terminal A is provided with the P-channel transistor  21 ; on the other hand, the terminal B is provided with the N-channel transistor  22 . The source and gate of the N-channel transistor  22  are connected, that is, diode-connected. 
   The terminal A is connected with the source of the P-channel transistor  21 , and the gate of the P-channel transistor is connected to the output of an inverter circuit  23 . The input of the inverter circuit  23  is connected to the terminal A. The back gate and drain of the P-channel transistor  21  are interconnected. The inverter circuit  23  comprises a CMOS circuit, and is connected to first power supply potential Vcc and reference potential Vss (e.g., ground potential). 
   The terminal B is connected with the source of the N-channel transistor  22 . The source and gate of the N-channel transistor  22  are interconnected, that is, diode-connected. The well voltage (back gate voltage) of the N-channel transistor  22  is reference voltage Vss; for example, ground potential. The voltage of the common drain of interconnected P-channel and N-channel transistors  21  and  22  is applied as well voltage VB to the well of the P-channel transistor  10 . The threshold Vthn of the N-channel transistor  22  is about 0.2 V to 0.3 V, for example. The threshold Vthp of the P-channel transistor  21  is about 0.6 V, for example. P-channel and N-channel transistors  21  and  22  constituting the well voltage generator circuit are provided for generating the well voltage. The current flow rate is relatively low; therefore, the P-channel and N-channel transistors  21  and  22  form a low-consumption type circuit. 
   The operation of the well voltage generator circuit shown in  FIG. 3  will be explained below. If the voltage Vpp of the terminal A is higher than the voltage Vcc of the terminal B, that is, Vpp≧Vcc, the P-channel transistor  21  turns on while the N-channel transistor  22  turns off. Thus, the output voltage of the potential switching circuit  20 , that is, the controlled boosted potential Vpp′ is equal to Vpp (Vpp′=Vpp). Therefore, the well voltage VB is equal to Vpp (VB=Vpp). 
   For example, a great many cells are operated; for this reason, a large current flows through the power supply supplying the voltage Vpp to the terminal A, or noise is generated. In this case, the boosted potential Vpp becomes low. When the voltage Vpp becomes lower than (Vcc−Vthn), the N-channel transistor  22  comprising a transistor having a low threshold voltage turns on, and When the voltage Vpp becomes lower than the circuit threshold of the inverter circuit  23 , the P-channel transistor  21  turns off. For this reason, the controlled boosted potential Vpp′ has the relationship of Vpp′=Vcc−Vthn; therefore, it is equal approximately to power supply potential Vcc. In other words, the well voltage VB has the relationship of VB=Vcc−Vthn; therefore, it is equal approximately to power supply potential Vcc. As a result, the PN junction between the source and well is prevented from being forward-biased; therefore, it is also prevented from turning on. Consequently, it is possible to prevent the influence on semiconductor elements. 
   In the well voltage generator circuit shown in  FIG. 3 , since the N-channel transistor  22  comprises a transistor having a low threshold voltage, when the boosted potential Vpp falls, and the N-channel transistor  22  turns on and the P-channel transistor  21  turns off, the controlled boosted potential Vpp′, that is, well voltage VB is equal to the source potential Vcc of the N-channel transistor  22  (strictly, Vcc−Vthn). As a result, the PN junction between the source and well is prevented from being forward-biased; therefore, it is also prevented from turning on. 
   If the well voltage VB is lower than the source voltage VS, a slight charge may flow through the PN junction between source and well, even if the difference between well voltage VB and source voltage VS is less than the threshold voltage of the PN junction between source and well. However, a large number of carriers are not generated in the substrate. Thus, neither parasitic transistors latch up nor a large current flows therethrough. Therefore, no influence is given on elements. 
   The well voltage generator circuit shown in  FIG. 3  is realized using a relatively simple configuration; therefore, it can be arranged in a small space, and it is effective in circuit arrangement. In addition, the well voltage generator circuit shown in  FIG. 3  is located near a transistor  10 ; therefore, it is possible to reduce malfunction by signal delay and distribution, and it is effective in the circuit operation. Incidentally, the well voltage generator circuit shown in  FIG. 3  may be located for each of several transistors  10 , or one circuit may be located with respect to the entirety of several transistors  10 . 
   (Second Embodiment) 
     FIG. 4  is a circuit diagram showing the semiconductor device according to a second embodiment of the present invention. 
   In semiconductor memory devices, a control circuit controlling memory cells is formed around the memory cells. The control circuit comprises elements such as a transistor or diode. Similarly to the first embodiment, the control circuit is composed of a P-channel transistor  10  shown in  FIG. 1 , for example. The P-channel transistor  10  is formed in a substrate or well formed in the substrate, and supplied with well voltage (back gate voltage) VB in addition to gate voltage VG, source voltage VS and drain voltage VD. The voltage VB is not limited to the well voltage, and a substrate voltage may be supplied. 
   As illustrated in  FIG. 2 , the P-channel transistor  10  comprises first semiconductor region  11 , P-type second semiconductor regions  12 ,  13 , and gate electrode  14 . The first semiconductor region  11  is formed of an N-type well or N-type semiconductor substrate. The P-type second semiconductor regions  12  and  13  are formed in the first semiconductor region  11 , and constitute source and drain regions of the P-channel transistor  10 . The gate electrode  14  is formed on the first semiconductor region  11  via a gate insulating film. The gate electrode  14 , second semiconductor regions  12 ,  13  and first semiconductor regions  11  are supplied with gate voltage VG, source voltage VS, drain voltage VD and well voltage VB, respectively. 
   Controlled boosted potential Vpp′ is supplied as the well voltage VB of the P-channel transistor  10 . A well voltage generator circuit shown in  FIG. 4  generates the controlled boosted potential Vpp′. The well voltage generator circuit is provided with terminals A and B. The terminal A receives boosted potential Vpp supplied from a second power supply comprising a charge pump circuit (not shown) in the semiconductor memory device. On the other hand, the terminal B receives power supply potential Vcc supplied from a first power supply. The controlled boosted potential Vpp′ is outputted from an output terminal. A potential switching circuit  20  is interposed between the terminals A and B. The potential switching circuit  20  has the configuration in which a P-channel transistor  21  and an N-channel transistor  22  are connected in series between the terminals A and B. The terminal A is provided with the P-channel transistor  21 ; on the other hand, the terminal B is provided with the N-channel transistor  22 . The back gate and drain of the P-channel transistor  21  are interconnected. The source and gate of the N-channel transistor  22  are connected, that is, diode-connected. 
   The terminal A is connected with the source of the P-channel transistor  21 , and the gate of the P-channel transistor  21  is connected with the output of a comparator circuit  24 . The comparator circuit  24  comprises a differential amplifier circuit  25  including a current mirror circuit as a load. The current mirror circuit is composed of two P-channel transistors  31  and  32 . The input section of the differential amplifier circuit  25  includes two differential transistors  33  and  34  each comprising an N-channel transistor. The input (gate) of the differential transistor  33  of the differential amplifier circuit is connected to the terminal A, and inputted with boosted potential Vpp. The input (gate) of the differential transistor  34  of the differential amplifier circuit is connected to the drain of an N-channel transistor  26 , and inputted with potential Vcc−Vthn via the N-channel transistor  26 . Vthn is the threshold value of the N-channel transistor  26 . The potential Vcc−Vthn is generated when power supply potential Vcc is connected to the source of the N-channel transistor  26  having connected source and gate. 
   The terminal B is connected with the source of the N-channel transistor  22 . The source and gate of the N-channel transistor  22  are interconnected, that is, diode-connected. The well voltage (back gate voltage) of the N-channel transistor  22  is reference voltage Vss; for example, ground potential. The voltage of the common drain of interconnected P-channel and N-channel transistors  21  and  22  is applied as well voltage VB to the well of the P-channel transistor  10 . The threshold voltage Vthn of the N-channel transistor  22  is lower than the threshold voltage Vthp of the P-channel transistor  21 . The threshold Vthn of the N-channel transistor  22  is about 0.2 V to 0.3 V, for example. The threshold Vthp of the P-channel transistor  21  is about 0.6 V, for example. N-channel transistor  22  of the potential switching circuit  20  and N-channel transistor  26  of the input section of the differential amplifier circuit  25  have substantially the same size and substantially the same threshold. P-channel and N-channel transistors  21  and  22  constituting the well voltage generator circuit are provided for generating the well voltage. The current flow rate is relatively low; therefore, the P-channel and N-channel transistors  21  and  22  form a low-consumption type circuit. 
   The operation of the well voltage generator circuit shown in  FIG. 4  will be explained below. If the voltage Vpp of the terminal A is higher than the voltage Vcc of the terminal B, that is, Vpp≧Vcc−Vthn, the P-channel transistor  21  turns on while the N-channel transistor  22  turns off. Thus, the output voltage of the potential switching circuit  20 , that is, the controlled boosted potential Vpp′ is equal to Vpp (Vpp′=Vpp). Therefore, the well voltage VB is equal to Vpp (VB=Vpp). 
   For example, a great many cells are operated; for this reason, a large current flows through the power supply supplying the voltage Vpp to the terminal A, or noise is generated. In this case, the boosted potential Vpp becomes low. In the comparator circuit  24 , when the boosted potential Vpp becomes low, and a difference occurs in the input voltage to differential transistors  33  and  34 , the output current increases or decreases so that the current ratio of differential transistors  33  and  34  can be kept constant in the comparator circuit  24 . The current from P-channel transistors  31  and  32  constituting the current mirror circuit is distributed to current flowing to differential transistors  33  and  34  and output current flowing to the out terminal. Therefore, the output current becomes constant regardless of the load connected to the output terminal. The difference of the input voltage to differential transistors  33  and  34  is the output voltage, and the amplification degree can be controlled from the external device. 
   The comparator circuit  24  outputs an “H” level when the boosted potential Vpp is lower than a predetermined level. More specifically, when Vpp is lower than Vcc−Vthn, the comparator circuit  24  outputs an “H” level. On the other hand, when boosted potential Vpp is higher than the predetermined level, the comparator circuit  24  outputs an “L” level. In other words, when Vpp is higher than Vcc−Vthn, the comparator circuit  24  outputs an “L” level. Thus, the boosted potential Vpp falls, and the N-channel transistor  22  comprising a transistor having a low threshold value turns on while the P-channel transistor  21  turns off. Therefore, the controlled boosted potential Vpp′ has the relationship of Vpp′=Vcc−Vthn, that is, equal approximately to power supply potential Vcc. In other words, the well voltage VB has the relationship of VB=Vcc−Vthn; therefore, it is equal approximately to power supply potential Vcc. Since the N-channel transistor is formed of a transistor having a low threshold, the PN junction between the source and well is prevented from being forward-biased; therefore, it is also prevented from turning on. 
   In the well voltage generator circuit shown in  FIG. 4 , since the N-channel transistor comprises a transistor having a low threshold voltage, when the boosted potential Vpp falls, and the N-channel transistor  22  turns on and the P-channel transistor  21  turns off, the controlled boosted potential Vpp′, that is, well voltage VB is equal to the source potential Vcc of the N-channel transistor  22  (strictly, Vcc−Vthn). As a result, the PN junction between the source and well is prevented from being forward-biased; therefore, it is also prevented from turning on. Consequently, it is possible to prevent the influence on semiconductor elements. 
   If the well voltage VB is lower than the source voltage VS, a slight charge may flow through the PN junction between source and well, even if the difference between well voltage VB and source voltage VS is less than the threshold voltage of the PN junction between source and well. However, a large number of carriers are not generated in the substrate. Thus, neither parasitic transistors latch up nor a large current flows therethrough. Therefore, no influence is given on elements. 
   With the embodiment, when the boosted potential Vpp falls and the N-channel transistor  22  comprising a transistor having a low threshold value turns on, the P-channel transistor  21  turns off. As the result, floating of the potential does not occur. 
   According to the embodiments described above, even if the boosted potential Vpp falls, the PN junction between source and well (or substrate) is prevented from being forward-biased, so that it can be prevented from turning on. As a result, it is possible to prevent the influence on semiconductor elements. 
   Additional advantages and modifications will readily occur to those skilled in the art. Therefore, the invention in its broader aspects is not limited to the specific details and representative embodiments shown and described herein. Accordingly, various modifications may be made without departing from the spirit or scope of the general inventive concept as defined by the appended claims and their equivalents.