Patent Publication Number: US-2002011885-A1

Title: Power model for EMI simulation to semiconductor integrated circuit , method of designing the power model, EMI simulator, power model preparation computer program, and storage medium storing the same as well as power model design support system

Description:
BACKGROUND OF THE INVENTION  
       [0001] The present invention relates to a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit and a method of designing the power model as well as an electro-magnetic interference simulator having the power model, and a power model preparation computer program for generating the power model and a storage medium for storing the power model preparation computer program and further a power model design support system for designing the power model, and more particularly to a transistor description large scale integration power model for an electro-magnetic interference simulation to a semiconductor integrated circuit and a method of designing the transistor description large scale integration power model as well as an electro-magnetic interference simulator having the transistor description large scale integration power model, and a transistor description large scale integration power model preparation computer program for generating the power model and a storage medium for storing the transistor description large scale integration power model preparation computer program and further a transistor description large scale integration power model design support system for designing the transistor description large scale integration power model.  
       [0002] The conventional techniques relative to the above are disclosed in the following four documents, for example, Nikkei Electronics 1998, 4-6, Apr. 6, 1998, p. 143, 111, (hereinafter referred to as a first applicant&#39;s admitted prior art), and IEC TC93 New York Item Proposal, May 15, 1997 entitled “Models of Integrated Circuits for EMI Behavioral Simulation” (hereinafter referred to as a second applicant&#39;s admitted prior art), and Japanese laid-open patent publication No. 10-54865 (hereinafter referred to as a third applicant&#39;s admitted prior art), and Japanese laid-open patent publication No. 11-120214 (hereinafter referred to as a fourth applicant&#39;s admitted prior art).  
       [0003] In order to suppress an electromagnetic radiation noise from being generated from electric, electronic and electron devices, it is effective to take certain countermeasures against the generation of the electromagnetic radiation noise in the design step. For this reason, a major of circuit designers introduced an electro-magnetic interference simulator for their design work.  
       [0004] Actually, however, it often appears that the actually measured value does not correspond to the simulated value. One cause is that the most of the simulators does not analyze the power system of the circuit. An input/output buffer information specification (IBIS) model is one of the typical device models to be used in the electromagnetic interference (EMI) simulator. The input/output buffer information specification (IBIS) model are that the input buffer and the output buffer are modeled. The electro-magnetic interference (EMI) simulator is based upon a simulation program with integrated circuit emphasis (SPICE) which is one of the circuit simulators, wherein models of the circuit elements are incorporated to calculate current values, so that a radiation electro-magnetic field is calculated from the current values.  
       [0005] The conventional electro-magnetic interference (EMI) simulation model 1  for the large scale integrated circuit depends upon the signal-base analysis of the large scale integrated circuit with excluding power terminals and ground terminals from the circuit elements.  
       [0006] The power of the large scale integrated circuit is connected not only to the input/output buffers but also to internal circuits not directly relative to signal terminals, wherein currents flowing through the internal circuits include high frequency components, for which reason it is undesirable to ignore the radiation electromagnetic field due to the power current. In order to analyze the electromagnetic interference (EMI) of the electric, electronic and electron devices, it is essential to analyze the power current of the printed board for analysis of the radiation electro-magnetic field due to the power current.  
       [0007] In order to analyze the electro-magnetic interference (EMI) on the printed board, a model of the large scale integrated circuit mounted on the printed board is necessary in addition to a transmission lines of the printed board. The format of the large scale integrated circuit model is classified into a transistor description format and an operational level description format. The transistor description format is that the internal circuit configurations of the large scale integrated circuit are accurately described with transistor models, interconnection resistance models and capacitance models. The transistor description format is generally used for designing the large scale integrated circuit. The operational level description format is that the transistor description format is simplified. The operational level description format is generally used for noise certification of the printed board. The above described input/output buffer information specification (IBIS) model is described in the operational level description format. The analysis of the radiation electromagnetic field from the power current will be described in the above two different formats.  
       [0008] The transistor description formation is used to find the power current for analysis of the radiation electromagnetic field. It is necessary to analyze the entire circuit configurations of the large scale integrated circuit even the circuit scale is tremendously large. FIG. 1 is a schematic view illustrative of an equivalent circuit of a conventional power model in the transistor description format for the electromagnetic interference (EMI) simulation of the semiconductor integrated circuit. The power model  38  in the transistor description format for the electromagnetic interference (EMI) simulation of the semiconductor integrated circuit has a first power terminal  39 , a second power terminal  40 , and arrays of transistor blocks  40 . A relatively small circuit scale, for example, a mask programmable read only memory needs about 5,000 transistors. A relatively large circuit scale, for example, a micro processor unit needs not less than about 1,000,000 transistors.  
       [0009] If, in accordance with the traditional signal-base analysis, the analysis only to the signal terminals is made, it is possible that the circuit models of the large scale integrated circuit is simplified into the input/output buffers only. Notwithstanding, in accordance with the analysis in the transistor description format, it is impossible to omit the circuits because all of the circuits are connected directly or indirectly to the power terminals. For this reason, a total amount of calculations by the electromagnetic interference (EMI) simulator is tremendously larger than the traditional signal-base analysis. This makes it difficult or impossible to conduct the analysis. Further, it is necessary for the user to receive the large scale integrated circuit model from the maker who manufactures the large scale integrated circuit. Notwithstanding, the transistor description format model includes many confidential informations of the maker, for example, informations about transistor structure, manufacturing processes, and internal circuit configurations of the large scale integrated circuit. The maker usually hesitates to provide the user with the transistor description format model.  
       [0010] The following model was proposed for analysis of the radiation electromagnetic field in the operational level description format. FIG. 2 is a schematic view illustrative of an equivalent circuit of a conventional power model in the operational level description format for the electromagnetic interference (EMI) simulation of the semiconductor integrated circuit, wherein the model comprises a current source and an impedance connected to the current source. A power model  42  for the electro-magnetic interference (EMI) simulation of the large scale integrated circuit has a first power terminal  39 , a second power terminal  40 , a current source  43  connected between the first and second power terminals  39  and  40 , and an impedance  44  connected in parallel to the current source  43  and between the first and second power terminals  39  and  40 , wherein the impedance  44  is connected across the current source  43 . A display  45  displays a power current waveform from the current source, wherein a vertical axis represents an amplitude and a horizontal axis represents time. This method is, however, engaged with the following problems.  
       [0011] The internal impedance of the power terminal of the large scale integrated circuit varies depending upon inputs of signals and voltages of the power terminals. The variations in the internal impedance or resistance makes complicated current waveforms. In order to find a power current waveform of the power current, it is necessary to measure currents flowing from the power terminals in the actual circuit and convert the measured current values into the current waveform. The conversion method of converting the measured current values into the current waveform is not so difficult because the analysis in a frequency region causes that as the frequency is constant, the impedance is also constant.  
       [0012] However, if the analysis is made in the time region, then the impedance varies over time and not constant, whereby the conversion method is very complicated. It is difficult to find the current waveform of the current source on the basis of the time region.  
       [0013] If the current waveform is actually measured for finding the current waveform of the large scale integrated circuit, the current waveform includes informations about impedance of the DC power circuit. The impedance in the circuit is also present in the model, for which reason the effect of the impedance is doubly considered, whereby the obtainable current waveform is made inaccurate.  
       [0014] If in order to find the accurate current value of the power terminal, the simulation is made in accordance with the transistor description format model, then the above described problems are also raised.  
       [0015] In summery to the above descriptions, the first problem is that the conventional transistor description format large scale integrated circuit model is incapable of or is hard to the electromagnetic interference (EMI) simulation to the power system of the large scale integrated circuit, because the circuit scale of the large scale integrated circuit is tremendously large and it is difficult to omit the circuits for conducting the simulation as the analysis to the signal terminals.  
       [0016] The second problem is that the operational level description format large scale integrated circuit model is very hard to conduct the electromagnetic interference (EMI) simulation in the time region, because the internal impedance of the large scale integrated circuit varies over time or in the time region, whereby it is extremely difficult to represent the current waveform of the power source of the operational level description format large scale integrated circuit model.  
       [0017] The third problem is that the conventional electro-magnetic interference (EMI) simulation conducts the analysis in the inaccurate state, because as the large scale integrated circuit is in the actual operation state, only parts of the large scale integrated circuit are operated. Namely, the analysis is made depending upon the actually operated parts of the large scale integrated circuit but not entire of the circuit.  
       [0018] In the above circumstances, it had been required to develop a novel invention free from the above problem.  
       SUMMARY OF THE INVENTION  
       [0019] Accordingly, it is an object of the present invention to provide a novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit free from the above problems.  
       [0020] It is a further object of the present invention to provide a novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model allows an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0021] It is a still further object of the present invention to provide a novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model makes it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0022] It is yet a further object of the present invention to provide a novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to allow an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0023] It is a further more object of the present invention to provide a novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to make it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0024] It is moreover object of the present invention to provide a novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit free from the above problems.  
       [0025] It is still more object of the present invention to provide a novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the method allows an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0026] It is yet more object of the present invention to provide a novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the method makes it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0027] It is still further more object of the present invention to provide a novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to allow an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0028] It is yet further more object of the present invention to provide a novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to make it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0029] It is another object of the present invention to provide a novel electro-magnetic interference simulator using a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit free from the above problems.  
       [0030] It is further another object of the present invention to provide a novel electro-magnetic interference simulator using a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the electro-magnetic interference simulator allows an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0031] It is still another object of the present invention to provide a novel electro-magnetic interference simulator using a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the electro-magnetic interference simulator makes it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0032] It is yet another object of the present invention to provide a novel electro-magnetic interference simulator using a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to allow an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0033] It is more another object of the present invention to provide a novel electro-magnetic interference simulator using a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to make it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0034] It is a still further another object of the present invention to provide a novel power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit free from the above problems.  
       [0035] It is a yet further another object of the present invention to provide a novel power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model preparation computer program allows an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0036] It is furthermore another object of the present invention to provide a novel power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model preparation computer program makes it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0037] It is moreover another object of the present invention to provide a novel power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to allow an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0038] It is still moreover another object of the present invention to provide a novel power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to make it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0039] It is an additional object of the present invention to provide a novel storage medium for storing a power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit free from the above problems.  
       [0040] It is a further additional object of the present invention to provide a novel storage medium for storing a power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model preparation computer program allows an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0041] It is a still further additional object of the present invention to provide a novel storage medium for storing a power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model preparation computer program makes it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0042] It is yet a further additional object of the present invention to provide a novel storage medium for storing a power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to allow an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0043] It is a further more additional object of the present invention to provide a novel storage medium for storing a power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to make it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0044] It is also an additional object of the present invention to provide a novel power model design support system for supporting a design for a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit free from the above problems.  
       [0045] It is also an additional object of the present invention to provide a novel power model design support system for supporting a design for a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model allows an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0046] It is also an additional object of the present invention to provide a novel power model design support system for supporting a design for a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model makes it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0047] It is also an additional object of the present invention to provide a novel power model design support system for supporting a design for a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to allow an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0048] It is also an additional object of the present invention to provide a novel power model design support system for supporting a design for a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to make it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
       [0049] The novel electro-magnetic interference (EMI) simulation model in accordance with the present invention is represented in the transistor description format for conducting the simulation to the radiation electro-magnetic field generated on the printed board. This transistor description format large scale integrated circuit power model is largely reduced in the number of transistors constituting this model. The electro-magnetic interference (EMI) simulator utilizes this transistor description format large scale integrated circuit power model to find a power current which flows on an interconnection of a printed board. This transistor description format large scale integrated circuit power model is prepared by extracting operating parts from a net-list for the large scale integrated circuit to reduce the number of transistors constituting this model. Non-operating parts of the large scale integrated circuit are simplified to be incorporated into the model. Namely, the transistor description format large scale integrated circuit power model includes the operating parts extracted from the net-list and the simplified non-operating parts, so that all of the parts of the large scale integrated circuit are utilized to prepare the transistor description format large scale integrated circuit power model.  
       [0050] The above and other objects, features and advantages of the present invention will be apparent from the following descriptions.  
     
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS  
     [0051] Preferred embodiments according to the present invention will be described in detail with reference to the accompanying drawings.  
     [0052]FIG. 1 is a schematic view illustrative of an equivalent circuit of a conventional power model in the transistor description format for the electro-magnetic interference (EMI) simulation of the semiconductor integrated circuit.  
     [0053]FIG. 2 is a schematic view illustrative of an equivalent circuit of a conventional power model in the operational level description format for the electro-magnetic interference (EMI) simulation of the semiconductor integrated circuit.  
     [0054]FIG. 3 is a circuit diagram illustrative of a first novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a first embodiment in accordance with the present invention.  
     [0055]FIG. 4 is a circuit diagram illustrative of a second novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a second embodiment in accordance with the present invention.  
     [0056]FIG. 5 is a circuit diagram illustrative of a third novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a third embodiment in accordance with the present invention.  
     [0057]FIG. 6 is a circuit diagram illustrative of a fourth novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a fourth embodiment in accordance with the present invention.  
     [0058]FIG. 7 is a circuit diagram illustrative of a fifth novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a fifth embodiment in accordance with the present invention.  
     [0059]FIG. 8 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into a single gate circuit, wherein the novel processes are involved in a first novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a sixth embodiment in accordance with the present invention.  
     [0060]FIG. 9 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into two-stage gate circuits, wherein the novel processes are involved in the first novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a seventh embodiment in accordance with the present invention.  
     [0061]FIG. 10 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into a single gate circuit, wherein the novel processes are involved in a second novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in an eighth embodiment in accordance with the present invention.  
     [0062]FIG. 11 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into two-stage gate circuits, wherein the novel processes are involved in a second novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a ninth embodiment in accordance with the present invention.  
     [0063]FIG. 12 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into a single gate circuit, wherein the novel processes are involved in a third novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a tenth embodiment in accordance with the present invention.  
     [0064]FIG. 13 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into two-stage gate circuits, wherein the novel processes are involved in a third novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in an eleventh embodiment in accordance with the present invention.  
     [0065]FIG. 14 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into a single gate circuit, wherein the novel processes are involved in a fourth novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a twelfth embodiment in accordance with the present invention.  
     [0066]FIG. 15 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into two-stage gate circuits, wherein the novel processes are involved in a fourth novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a thirteenth embodiment in accordance with the present invention.  
     [0067]FIG. 16 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into a single gate circuit, wherein the novel processes are involved in a fifth novel method of designing a power model for an electromagnetic interference simulation to a semiconductor integrated circuit in a fourteenth embodiment in accordance with the present invention.  
     [0068]FIG. 17 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into two stage gate circuits, wherein the novel processes are involved in a fifth novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a fifteenth embodiment in accordance with the present invention.  
     [0069]FIG. 18 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into an equivalent internal capacitive part, wherein the novel processes are involved in the first novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a sixteenth embodiment in accordance with the present invention.  
     [0070]FIG. 19 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into an equivalent internal capacitive part, wherein the novel processes are involved in the second novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a seventeenth embodiment in accordance with the present invention.  
     [0071]FIG. 20 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into an equivalent internal capacitive part, wherein the novel processes are involved in the third novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in an eighteenth embodiment in accordance with the present invention.  
     [0072]FIG. 21 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into an equivalent internal capacitive part, wherein the novel processes are involved in the fourth novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a nineteenth embodiment in accordance with the present invention.  
     [0073]FIG. 22 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into an equivalent internal capacitive part, wherein the novel processes are involved in the fifth novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a twentieth embodiment in accordance with the present invention.  
     [0074]FIG. 23 is a block diagram illustrative of a support system for designing a power model in a twenty first embodiment according to the present invention.  
     [0075]FIG. 24 is a flow chart illustrative of the electromagnetic interference simulation to the semiconductor integrated circuit by use of a simulator on the basis of the first and second novel power models shown in FIGS. 3 and 4 and prepared by the first, second, third, fourth and fifth design methods executed by the supporting system shown in FIG. 23.  
     [0076]FIG. 25 is a circuit diagram illustrative of a modeled circuit board connected to the novel power model for the electromagnetic interference simulation in accordance with the present invention.  
     [0077]FIG. 26 is a circuit diagram illustrative of a modeled semiconductor integrated circuit for the electromagnetic interference simulation in accordance with the present invention.  
     [0078]FIG. 27 is a diagram illustrative of variations in currents over frequency to show frequency spectrums which has been transformed by Fourier-transform from a current waveform which represents variation in current over time at a fixed point of a circuit board, wherein  represents an actually measured value, whilst ◯ represents an analyzed value.  
    
    
     DISCLOSURE OF THE INVENTION  
     [0079] The novel electro-magnetic interference (EMI) simulation model in accordance with the present invention is represented in the transistor description format for conducting the simulation to the radiation electro-magnetic field generated on the printed board. This transistor description format large scale integrated circuit power model is largely reduced in the number of transistors constituting this model. The electro-magnetic interference (EMI) simulator utilizes this transistor description format large scale integrated circuit power model to find a power current which flows on an interconnection of a printed board. This transistor description format large scale integrated circuit power model is prepared by extracting operating parts from a net-list for the large scale integrated circuit to reduce the number of transistors constituting this model. Non-operating parts of the large scale integrated circuit are simplified to be incorporated into the model. Namely, the transistor description format large scale integrated circuit power model includes the operating parts extracted from the net-list and the simplified non-operating parts, so that all of the parts of the large scale integrated circuit are utilized to prepare the transistor description format large scale integrated circuit power model.  
     [0080] In accordance with the present invention, the power system of the large scale integrated circuit is modeled into an inverter circuit and an equivalent capacity. As compared to the conventional transistor description format large scale integrated circuit power model, a calculation load to the electro-magnetic interference (EMI) simulator is reduced, thereby making it easy to conduct the power current analysis. The non-operating parts of the large scale integrated circuit are considered on the electro-magnetic interference (EMI) simulation, whereby the large scale integrated circuit model shows similar operations or behaviors to the actual operations or behaviors of the actual large scale integrated circuit. This makes it possible to find a highly accurate power current of the large scale integrated circuit. Since the confidential detailed informations about the internal circuit configurations of the large scale integrated circuit and the device structures are not included in this transistor description format large scale integrated circuit power model, the maker who manufactures the large scale integrated circuit is likely to show this transistor description format large scale integrated circuit power model to the user with keeping the detailed informations to be confidential.  
     [0081] The first present invention provides a power model for a semiconductor integrated circuit, wherein the power model comprises a logic gate circuit part representing an operating part of the semiconductor integrated circuit and an equivalent internal capacitive part representing a non-operating part of the semiconductor integrated circuit.  
     [0082] It is also preferable that the power model is independently provided for each of plural power systems which are independent from each other and included in the semiconductor integrated circuit.  
     [0083] It is also preferable that internal circuit configurations of the semiconductor integrated circuit are divided into plural blocks on the basis of arrangement informations, and the power model is provided for each of the plural blocks.  
     [0084] It is also preferable that internal circuit configurations of the semiconductor integrated circuit are divided into plural groups, each of the plural groups comprises a same timing group which includes logic gate circuits having individual signal transmission delay times fallen in a group-belonging predetermined time range which belongs to each of the plural groups, and the power model is provided for each of the plural groups.  
     [0085] It is also preferable that the power model further comprises a signal source connected to the logic gate circuit part for supplying a frequency-fixed signal to the logic gate circuit part, so that the logic gate circuit part represents operating state parts of the semiconductor integrated circuit in accordance with the frequency-fixed signal, and the equivalent internal capacitive part represents non-operating state parts of the semiconductor integrated circuit.  
     [0086] It is also preferable that the equivalent internal capacitive part further represents operating-irrelevant fixed parts of the semiconductor integrated circuit.  
     [0087] It is also preferable that the logic gate circuit part is connected between first and second powers, and the equivalent internal capacitive part is also connected between the first and second powers.  
     [0088] It is also preferable that the logic gate circuit part further comprises a single pair of an inverter circuit and a load capacitive element, and the inverter circuit is connected between the first and second powers and the load capacitive element is also connected between the first and second powers, and the load capacitive element is placed between the inverter circuit and the equivalent internal capacitive part.  
     [0089] It is also preferable that the load capacitive element comprises a series connection of a first load capacitance and a second load capacitance between the first and second powers, and an intermediate point between the first and second load capacitances is connected to an output terminal of the inverter circuit.  
     [0090] It is also preferable that the equivalent internal capacitive part further comprises at least an equivalent internal capacitive element connected between the first and second powers.  
     [0091] It is also preferable that a plurality of the equivalent internal capacitive element is connected between the first and second powers, and the equivalent internal capacitive element comprises a series connection of a capacitance and a resistance between the first and second powers.  
     [0092] It is also preferable that the inverter circuit comprises a series connection of a p-channel MOS field effect transistor and an n-channel MOS field effect transistor, and gate electrodes of the p-channel and n-channel MOS field effect transistors are connected to a clock signal source for applying a clock signal to the gate electrodes of the p-channel and n-channel MOS field effect transistors.  
     [0093] It is also preferable that the logic gate circuit part further comprises plural pairs of an inverter circuit and a load capacitive element, and the inverter circuit is connected between the first and second powers and the load capacitive element is also connected between the first and second powers, and in each pair, the load capacitive element is placed closer to the equivalent internal capacitive part than the inverter circuit.  
     [0094] It is also preferable that the load capacitive element comprises a series connection of a first load capacitance and a second load capacitance between the first and second powers, and an intermediate point between the first and second load capacitances is connected to an output terminal of the inverter circuit.  
     [0095] It is also preferable that the equivalent internal capacitive part further comprises at least an equivalent internal capacitive element connected between the first and second powers.  
     [0096] It is also preferable that a plurality of the equivalent internal capacitive element is connected between the first and second powers, and the equivalent internal capacitive element comprises a series connection of a capacitance and a resistance between the first and second powers.  
     [0097] It is also preferable that the inverter circuit comprises a series connection of a p-channel MOS field effect transistor and an n-channel MOS field effect transistor, and gate electrodes of the p-channel and n-channel MOS field effect transistors are connected to a clock signal source for applying a clock signal to the gate electrodes of the p-channel and n-channel MOS field effect transistors.  
     [0098] It is also preferable that the equivalent internal capacitive part is placed between the logic gate circuit part and a power system side.  
     [0099] It is also preferable that the power model is deigned for simulation to a current distribution over a circuit board on which the semiconductor integrated circuit is mounted.  
     [0100] It is also preferable that the power model is deigned for an electro-magnetic interference simulation to an electromagnetic field distribution over a circuit board on which the semiconductor integrated circuit is mounted.  
     [0101] The second present invention provides a method of designing a power model for a semiconductor integrated circuit. The power model comprises a logic gate circuit part and an equivalent internal capacitive part, wherein operating-related informations of all gate circuits constituting the semiconductor integrated circuit are utilized in first sequential processes to prepare the logic gate circuit part of the power model, and wherein non-operating-related informations of the all gate circuits constituting the semiconductor integrated circuit are utilized in second sequential processes separated from the first sequential processes to prepare the equivalent internal capacitive part of the power model.  
     [0102] It is also preferable that in the first sequential processes, informations about gate widths of operating-state p-channel transistors in the operating-state of the constituting gate circuits are utilized to decide a gate width of a model p-channel transistor; informations about gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits are utilized to decide a gate width of a model n-channel transistor; informations about gate capacities of the operating-state p-channel transistors in the operating-state of the constituting gate circuits and about interconnection capacitances between the operating-state p-channel transistors and a first power are utilized to decide a model first load capacity; and informations about gate capacities of the operating-state n-channel transistors in the operating-state of the constituting gate circuits and about interconnection capacitances between the operating-state n-channel transistors and a second power are utilized to decide a model second load capacity, whereby the logic gate circuit part comprising at least a pair of p-channel and n-channel transistors and at least a pair of first and second load capacities is designed.  
     [0103] It is also preferable that a sum of gate widths of the operating-state p-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a sum of gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a sum of gate capacitances of the operating-state p-channel transistors and interconnection capacitances between the operating-state p-channel transistors and the first power is defined to be a model first load capacity; and a sum of gate capacitances of the operating-state n-channel transistors and interconnection capacitances between the operating-state n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0104] It is also preferable that a half of a sum of gate widths of the operating-state p-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a sum of gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a sum of gate capacitances of the operating-state p-channel transistors and interconnection capacitances between the operating-state p-channel transistors and the first power is defined to be a model first load capacity and a half of a sum of gate capacitances of the operating-state n-channel transistors and interconnection capacitances between the operating-state n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0105] It is also preferable that a product of the number of the operating-state gate circuits and an averaged value of gate widths of the operating-state p-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a product of the number of the operating-state gate circuits and an averaged value of gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a product of the number of the operating-state gate circuits and a sum of both a first averaged value of gate capacitances of the operating-state p-channel transistors and a second averaged value of interconnection capacitances between the operating-state p-channel transistors and the first power is defined to be a model first load capacity; and a product of the number of the operating-state gate circuits and a sum of both a first averaged value of gate capacitances of the operating-state n-channel transistors and a second averaged value of interconnection capacitances between the operating-state n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0106] It is also preferable that a half of a product of the number of the operating-state gate circuits and an averaged value of gate widths of the operating-state p-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a product of the number of the operating-state gate circuits and an averaged value of gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a product of the number of the operating-state gate circuits and a sum of both a first averaged value of gate capacitances of the operating-state p-channel transistors and a second averaged value of interconnection capacitances between the operating-state p-channel transistors and the first power is defined to be a model first load capacity; and a half of a product of the number of the operating-state gate circuits and a sum of both a first averaged value of gate capacitances of the operating-state n-channel transistors and a second averaged value of interconnection capacitances between the operating-state n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0107] It is also preferable that in the first sequential processes, informations about gate widths of all p-channel transistors of the constituting gate circuits and an information about operational rate of operating-state p-channel transistors in the operating-state are utilized to decide a gate width of a model p-channel transistor; informations about gate widths of all n-channel transistors of the constituting gate circuits and an information about operational rate of operating-state n-channel transistors in the operating-state are utilized to decide a gate width of a model n-channel transistor; informations about gate capacities of the all p-channel transistors of the constituting gate circuits and informations about interconnection capacitances between the all p-channel transistors and a first power and informations about the operational rate are utilized to decide a model first load capacity; and informations about gate capacities of the all n-channel transistors of the constituting gate circuits and informations about interconnection capacitances between the all n-channel transistors and a second power and informations about the operational rate are utilized to decide a model second load capacity, whereby the logic gate circuit part comprising at least a pair of p-channel and n-channel transistors and at least a pair of first and second load capacities is designed.  
     [0108] It is also preferable that a product of the number of the all gate circuits, an average operational rate of the gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a product of the number of the all gate circuits, an average operational rate of the gate circuits, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a product of the number of the all gate circuits, an average operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a product of the number of the all gate circuits, an average operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0109] It is also preferable that a half of a product of the number of the all gate circuits, an average operational rate of the gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a product of the number of the all gate circuits, an average operational rate of the gate circuits, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a product of the number of the all gate circuits, an average operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a half of a product of the number of the all gate circuits, an average operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0110] It is also preferable that a product of the number of the all gate circuits, a maximum operational rate of the gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0111] It is also preferable that a half of a product of the number of the all gate circuits, a maximum operational rate of the gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a half of a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0112] It is also preferable that in the first sequential processes, informations about gate widths of all p-channel transistors of the constituting gate circuits and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide a gate width of a model p-channel transistor; informations about gate widths of all n-channel transistors of the constituting gate circuits and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide a gate width of a model n-channel transistor; informations about gate capacities of the all p-channel transistors of the constituting gate circuits and informations about interconnection capacitances between the all p-channel transistors and a first power and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide a model first load capacity; and informations about gate capacities of the all n-channel transistors of the constituting gate circuits and informations about interconnection capacitances between the all n-channel transistors and a second power and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide a model second load capacity, whereby the logic gate circuit part comprising at least a pair of p-channel and n-channel transistors and at least a pair of first and second load capacities is designed.  
     [0113] It is also preferable that a product of the number of the all gate circuits, and a power current ratio of an averaged current value of the basic gate circuits to an averaged current value of the constituting gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a product of the number of the all gate circuits, the power current ratio, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a product of the number of the all gate circuits, the power current ratio, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a product of the number of the all gate circuits, the power current ratio, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0114] It is also preferable that a half of a product of the number of the all gate circuits, and a power current ratio of an averaged current value of the basic gate circuits to an averaged current value of the constituting gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a product of the number of the all gate circuits, the power current ratio, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a product of the number of the all gate circuits, the power current ratio, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a half of a product of the number of the all gate circuits, the power current ratio, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0115] It is also preferable that in the second sequential processes, informations about ON-resistances of non-operating-state transistors in the non-operating-state of the constituting gate circuits are utilized to decide an ON-resistance of an equivalent internal capacity; and informations about gate capacities of the non-operating-state transistors in the non-operating-state of the constituting gate circuits and about interconnection capacitances between the operating-state transistors and a power are utilized to decide the equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0116] It is also preferable that a double of a reciprocal of a sum of reciprocals of ON-resistances of non-operating p-channel transistors in the non-operating state is defined to be an ON-resistance of a third equivalent internal capacity; a double of a reciprocal of a sum of reciprocals of ON-resistances of non-operating n-channel transistors in the non-operating state is defined to be an ON-resistance of a second equivalent internal capacity; an arithmetic mean of a sum of gate capacities of the non-operating p-channel transistors and a sum of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and an arithmetic mean of a sum of gate capacities of the non-operating n-channel transistors and a sum of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0117] It is also preferable that a double of a product of an averaged value of ON-resistances of non-operating p-channel transistors in the non-operating state and a reciprocal of the number of non-operating gate circuits is defined to be an ON-resistance of a third equivalent internal capacity; a double of a product of an averaged value of ON-resistances of non-operating n-channel transistors in the non-operating state and a reciprocal of the number of the non-operating gate circuit is defined to be an ON-resistance of a second equivalent internal capacity; a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating p-channel transistors and an averaged value of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating n-channel transistors and an averaged value of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0118] It is also preferable that in the second sequential processes, informations about an averaged value of ON-resistances of all transistors included in the constituting gate circuits and the number of non-operating gate circuits are utilized to decide an ON-resistance of an equivalent internal capacity; and informations about an averaged value of gate capacities of the non-operating-state transistors in the non-operating-state of the constituting gate circuits, and the number of non-operating gate circuits as well as informations about an averaged value of interconnection capacitances between the operating-state transistors and a power are utilized to decide the equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0119] It is also preferable that the number of non-operating gate circuits in the non-operating state is defined to be a product of a total number of the constituting logic gate included in the semiconductor integrated circuit and a remainder by subtracting an average operational rate from 1; a double of a product of an averaged value of ON-resistances of non-operating p-channel transistors in the non-operating state and a reciprocal of the number of non-operating gate circuits is defined to be an ON-resistance of a third equivalent internal capacity; a double of a product of an averaged value of ON-resistances of non-operating n-channel transistors in the non-operating state and a reciprocal of the number of the non-operating gate circuit is defined to be an ON-resistance of a second equivalent internal capacity; a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating p-channel transistors and an averaged value of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating n-channel transistors and an averaged value of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0120] It is also preferable that the number of non-operating gate circuits in the non-operating state is defined to be a product of a total number of the constituting logic gate included in the semiconductor integrated circuit and a remainder by subtracting a maximum operational rate from 1; a double of a product of an averaged value of ON-resistances of non-operating p-channel transistors in the non-operating state and a reciprocal of the number of non-operating gate circuits is defined to be an ON-resistance of a third equivalent internal capacity; a double of a product of an averaged value of ON-resistances of non-operating n-channel transistors in the non-operating state and a reciprocal of the number of the non-operating gate circuit is defined to be an ON-resistance of a second equivalent internal capacity; a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating p-channel transistors and an averaged value of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating n-channel transistors and an averaged value of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0121] It is also preferable that informations about an averaged value of ON-resistances of all transistors included in the constituting gate circuits and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide an ON-resistance of an equivalent internal capacity; and informations about an averaged value of gate capacities of the non-operating-state transistors in the non-operating-state of the constituting gate circuits, and informations about currents of basic gate circuits and the constituting gate circuits as well as informations about an averaged value of interconnection capacitances between the operating-state transistors and a power are utilized to decide the equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0122] It is also preferable that the number of non-operating gate circuits in the non-operating state is defined to be a product of the total number of the constituting gate circuits included in the semiconductor integrated circuit and a power current ratio which is defined to be a ratio of an averaged current value of all of basic gate circuits to an averaged current value of all of the constituting gate circuits; a double of a product of an averaged value of ON-resistances of non-operating p-channel transistors in the non-operating state and a reciprocal of the number of non-operating gate circuits is defined to be an ON-resistance of a third equivalent internal capacity; a double of a product of an averaged value of ON-resistances of non-operating n-channel transistors in the non-operating state and a reciprocal of the number of the non-operating gate circuit is defined to be an ON-resistance of a second equivalent internal capacity; a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating p-channel transistors and an averaged value of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating n-channel transistors and an averaged value of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0123] It is also preferable that the equivalent internal capacitive part is placed between the logic gate circuit part and a power system side.  
     [0124] It is also preferable that the power model is deigned for simulation to a current distribution over a circuit board on which the semiconductor integrated circuit is mounted.  
     [0125] It is also preferable that the power model is deigned for an electro-magnetic interference simulation to an electromagnetic field distribution over a circuit board on which the semiconductor integrated circuit is mounted.  
     [0126] The third present invention provides a storage medium for storing a computer program for designing a power model for a semiconductor integrated circuit, and the power model comprises a logic gate circuit part and an equivalent internal capacitive part, wherein operating-related informations of all gate circuits constituting the semiconductor integrated circuit are utilized in first sequential processes to prepare the logic gate circuit part of the power model, and wherein non-operating-related informations of the all gate circuits constituting the semiconductor integrated circuit are utilized in second sequential processes separated from the first sequential processes to prepare the equivalent internal capacitive part of the power model.  
     [0127] It is also preferable that in the first sequential processes, informations about gate widths of operating-state p-channel transistors in the operating-state of the constituting gate circuits are utilized to decide a gate width of a model p-channel transistor; informations about gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits are utilized to decide a gate width of a model n-channel transistor; informations about gate capacities of the operating-state p-channel transistors in the operating-state of the constituting gate circuits and about interconnection capacitances between the operating-state p-channel transistors and a first power are utilized to decide a model first load capacity; and informations about gate capacities of the operating-state n-channel transistors in the operating-state of the constituting gate circuits and about interconnection capacitances between the operating-state n-channel transistors and a second power are utilized to decide a model second load capacity, whereby the logic gate circuit part comprising at least a pair of p-channel and n-channel transistors and at least a pair of first and second load capacities is designed.  
     [0128] It is also preferable that a sum of gate widths of the operating-state p-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a sum of gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a sum of gate capacitances of the operating-state p-channel transistors and interconnection capacitances between the operating-state p-channel transistors and the first power is defined to be a model first load capacity; and a sum of gate capacitances of the operating-state n-channel transistors and interconnection capacitances between the operating-state n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0129] It is also preferable that a half of a sum of gate widths of the operating-state p-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a sum of gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a sum of gate capacitances of the operating-state p-channel transistors and interconnection capacitances between the operating-state p-channel transistors and the first power is defined to be a model first load capacity; and a half of a sum of gate capacitances of the operating-state n-channel transistors and interconnection capacitances between the operating-state n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0130] It is also preferable that a product of the number of the operating-state gate circuits and an averaged value of gate widths of the operating-state p-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a product of the number of the operating-state gate circuits and an averaged value of gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a product of the number of the operating-state gate circuits and a sum of both a first averaged value of gate capacitances of the operating-state p-channel transistors and a second averaged value of interconnection capacitances between the operating-state p-channel transistors and the first power is defined to be a model first load capacity; and a product of the number of the operating-state gate circuits and a sum of both a first averaged value of gate capacitances of the operating-state n-channel transistors and a second averaged value of interconnection capacitances between the operating-state n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0131] It is also preferable that a half of a product of the number of the operating-state gate circuits and an averaged value of gate widths of the operating-state p-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a product of the number of the operating-state gate circuits and an averaged value of gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a product of the number of the operating-state gate circuits and a sum of both a first averaged value of gate capacitances of the operating-state p-channel transistors and a second averaged value of interconnection capacitances between the operating-state p-channel transistors and the first power is defined to be a model first load capacity; and a half of a product of the number of the operating-state gate circuits and a sum of both a first averaged value of gate capacitances of the operating-state n-channel transistors and a second averaged value of interconnection capacitances between the operating-state n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0132] It is also preferable that in the first sequential processes, informations about gate widths of all p-channel transistors of the constituting gate circuits and an information about operational rate of operating-state p-channel transistors in the operating-state are utilized to decide a gate width of a model p-channel transistor; informations about gate widths of all n-channel transistors of the constituting gate circuits and an information about operational rate of operating-state n-channel transistors in the operating-state are utilized to decide a gate width of a model n-channel transistor; informations about gate capacities of the all p-channel transistors of the constituting gate circuits and informations about interconnection capacitances between the all p-channel transistors and a first power and informations about the operational rate are utilized to decide a model first load capacity; and informations about gate capacities of the all n-channel transistors of the constituting gate circuits and informations about interconnection capacitances between the all n-channel transistors and a second power and informations about the operational rate are utilized to decide a model second load capacity, whereby the logic gate circuit part comprising at least a pair of p-channel and n-channel transistors and at least a pair of first and second load capacities is designed.  
     [0133] It is also preferable that a product of the number of the all gate circuits, an average operational rate of the gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a product of the number of the all gate circuits, an average operational rate of the gate circuits, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a product of the number of the all gate circuits, an average operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a product of the number of the all gate circuits, an average operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0134] It is also preferable that a half of a product of the number of the all gate circuits, an average operational rate of the gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a product of the number of the all gate circuits, an average operational rate of the gate circuits, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a product of the number of the all gate circuits, an average operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a half of a product of the number of the all gate circuits, an average operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0135] It is also preferable that a product of the number of the all gate circuits, a maximum operational rate of the gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0136] It is also preferable that a half of a product of the number of the all gate circuits, a maximum operational rate of the gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a half of a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0137] It is also preferable that in the first sequential processes, informations about gate widths of all p-channel transistors of the constituting gate circuits and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide a gate width of a model p-channel transistor; informations about gate widths of all n-channel transistors of the constituting gate circuits and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide a gate width of a model n-channel transistor; informations about gate capacities of the all p-channel transistors of the constituting gate circuits and informations about interconnection capacitances between the all p-channel transistors and a first power and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide a model first load capacity; and informations about gate capacities of the all n-channel transistors of the constituting gate circuits and informations about interconnection capacitances between the all n-channel transistors and a second power and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide a model second load capacity, whereby the logic gate circuit part comprising at least a pair of p-channel and n-channel transistors and at least a pair of first and second load capacities is designed.  
     [0138] It is also preferable that a product of the number of the all gate circuits, and a power current ratio of an averaged current value of the basic gate circuits to an averaged current value of the constituting gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a product of the number of the all gate circuits, the power current ratio, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a product of the number of the all gate circuits, the power current ratio, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a product of the number of the all gate circuits, the power current ratio, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0139] It is also preferable that a half of a product of the number of the all gate circuits, and a power current ratio of an averaged current value of the basic gate circuits to an averaged current value of the constituting gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a product of the number of the all gate circuits, the power current ratio, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a product of the number of the all gate circuits, the power current ratio, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a half of a product of the number of the all gate circuits, the power current ratio, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0140] It is also preferable that in the second sequential processes, informations about ON-resistances of non-operating-state transistors in the non-operating-state of the constituting gate circuits are utilized to decide an ON-resistance of an equivalent internal capacity; and informations about gate capacities of the non-operating-state transistors in the non-operating-state of the constituting gate circuits and about interconnection capacitances between the operating-state transistors and a power are utilized to decide the equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0141] It is also preferable that a double of a reciprocal of a sum of reciprocals of ON-resistances of non-operating p-channel transistors in the non-operating state is defined to be an ON-resistance of a third equivalent internal capacity; a double of a reciprocal of a sum of reciprocals of ON-resistances of non-operating n-channel transistors in the non-operating state is defined to be an ON-resistance of a second equivalent internal capacity; an arithmetic mean of a sum of gate capacities of the non-operating p-channel transistors and a sum of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and an arithmetic mean of a sum of gate capacities of the non-operating n-channel transistors and a sum of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0142] It is also preferable that a double of a product of an averaged value of ON-resistances of non-operating p-channel transistors in the non-operating state and a reciprocal of the number of non-operating gate circuits is defined to be an ON-resistance of a third equivalent internal capacity; a double of a product of an averaged value of ON-resistances of non-operating n-channel transistors in the non-operating state and a reciprocal of the number of the non-operating gate circuit is defined to be an ON-resistance of a second equivalent internal capacity; a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating p-channel transistors and an averaged value of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating n-channel transistors and an averaged value of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0143] It is also preferable that in the second sequential processes, informations about an averaged value of ON-resistances of all transistors included in the constituting gate circuits and the number of non-operating gate circuits are utilized to decide an ON-resistance of an equivalent internal capacity; and informations about an averaged value of gate capacities of the non-operating-state transistors in the non-operating-state of the constituting gate circuits, and the number of non-operating gate circuits as well as informations about an averaged value of interconnection capacitances between the operating-state transistors and a power are utilized to decide the equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0144] It is also preferable that the number of non-operating gate circuits in the non-operating state is defined to be a product of a total number of the constituting logic gate included in the semiconductor integrated circuit and a remainder by subtracting an average operational rate from 1; a double of a product of an averaged value of ON-resistances of non-operating p-channel transistors in the non-operating state and a reciprocal of the number of non-operating gate circuits is defined to be an ON-resistance of a third equivalent internal capacity; a double of a product of an averaged value of ON-resistances of non-operating n-channel transistors in the non-operating state and a reciprocal of the number of the non-operating gate circuit is defined to be an ON-resistance of a second equivalent internal capacity; a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating p-channel transistors and an averaged value of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating n-channel transistors and an averaged value of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0145] It is also preferable that the number of non-operating gate circuits in the non-operating state is defined to be a product of a total number of the constituting logic gate included in the semiconductor integrated circuit and a remainder by subtracting a maximum operational rate from 1; a double of a product of an averaged value of ON-resistances of non-operating p-channel transistors in the non-operating state and a reciprocal of the number of non-operating gate circuits is defined to be an ON-resistance of a third equivalent internal capacity; a double of a product of an averaged value of ON-resistances of non-operating n-channel transistors in the non-operating state and a reciprocal of the number of the non-operating gate circuit is defined to be an ON-resistance of a second equivalent internal capacity; a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating p-channel transistors and an averaged value of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating n-channel transistors and an averaged value of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0146] It is also preferable that informations about an averaged value of ON-resistances of all transistors included in the constituting gate circuits and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide an ON-resistance of an equivalent internal capacity; and informations about an averaged value of gate capacities of the non-operating-state transistors in the non-operating-state of the constituting gate circuits, and informations about currents of basic gate circuits and the constituting gate circuits as well as informations about an averaged value of interconnection capacitances between the operating-state transistors and a power are utilized to decide the equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0147] It is also preferable that the number of non-operating gate circuits in the non-operating state is defined to be a product of the total number of the constituting gate circuits included in the semiconductor integrated circuit and a power current ratio which is defined to be a ratio of an averaged current value of all of basic gate circuits to an averaged current value of all of the constituting gate circuits; a double of a product of an averaged value of ON-resistances of non-operating p-channel transistors in the non-operating state and a reciprocal of the number of non-operating gate circuits is defined to be an ON-resistance of a third equivalent internal capacity; a double of a product of an averaged value of ON-resistances of non-operating n-channel transistors in the non-operating state and a reciprocal of the number of the non-operating gate circuit is defined to be an ON-resistance of a second equivalent internal capacity; a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating p-channel transistors and an averaged value of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating n-channel transistors and an averaged value of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0148] It is also preferable that the equivalent internal capacitive part is placed between the logic gate circuit part and a power system side.  
     [0149] It is also preferable that the power model is deigned for simulation to a current distribution over a circuit board on which the semiconductor integrated circuit is mounted.  
     [0150] It is also preferable that the power model is deigned for an electromagnetic interference simulation to an electromagnetic field distribution over a circuit board on which the semiconductor integrated circuit is mounted.  
     [0151] The fourth present invention provides a supporting system for designing a power model for a semiconductor integrated circuit, and The power model comprises a logic gate circuit part and an equivalent internal capacitive part. The supporting system comprises : a data base storing informations of internal circuit configurations; a storage medium for storing informations about circuit elements and interconnections between the circuit elements of the power model as well as for storing a computer program for designing the power model; a processor being connected to the data base and the storage medium for executing the computer program to prepare the power model; and an output device being connected to the processor for outputting the power model prepared by the processor, wherein operating-related informations of all gate circuits constituting the semiconductor integrated circuit are utilized in first sequential processes to prepare the logic gate circuit part of the power model, and wherein non-operating-related informations of the all gate circuits constituting the semiconductor integrated circuit are utilized in second sequential processes separated from the first sequential processes to prepare the equivalent internal capacitive part of the power model.  
     [0152] It is also preferable that in the first sequential processes, informations about gate widths of operating-state p-channel transistors in the operating-state of the constituting gate circuits are utilized to decide a gate width of a model p-channel transistor; informations about gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits are utilized to decide a gate width of a model n-channel transistor; informations about gate capacities of the operating-state p-channel transistors in the operating-state of the constituting gate circuits and about interconnection capacitances between the operating-state p-channel transistors and a first power are utilized to decide a model first load capacity; and informations about gate capacities of the operating-state n-channel transistors in the operating-state of the constituting gate circuits and about interconnection capacitances between the operating-state n-channel transistors and a second power are utilized to decide a model second load capacity, whereby the logic gate circuit part comprising at least a pair of p-channel and n-channel transistors and at least a pair of first and second load capacities is designed.  
     [0153] It is also preferable that a sum of gate widths of the operating-state p-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a sum of gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a sum of gate capacitances of the operating-state p-channel transistors and interconnection capacitances between the operating-state p-channel transistors and the first power is defined to be a model first load capacity; and a sum of gate capacitances of the operating-state n-channel transistors and interconnection capacitances between the operating-state n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0154] It is also preferable that a half of a sum of gate widths of the operating-state p-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a sum of gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a sum of gate capacitances of the operating-state p-channel transistors and interconnection capacitances between the operating-state p-channel transistors and the first power is defined to be a model first load capacity; and a half of a sum of gate capacitances of the operating-state n-channel transistors and interconnection capacitances between the operating-state n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0155] It is also preferable that a product of the number of the operating-state gate circuits and an averaged value of gate widths of the operating-state p-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a product of the number of the operating-state gate circuits and an averaged value of gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a product of the number of the operating-state gate circuits and a sum of both a first averaged value of gate capacitances of the operating-state p-channel transistors and a second averaged value of interconnection capacitances between the operating-state p-channel transistors and the first power is defined to be a model first load capacity; and a product of the number of the operating-state gate circuits and a sum of both a first averaged value of gate capacitances of the operating-state n-channel transistors and a second averaged value of interconnection capacitances between the operating-state n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0156] It is also preferable that a half of a product of the number of the operating-state gate circuits and an averaged value of gate widths of the operating-state p-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a product of the number of the operating-state gate circuits and an averaged value of gate widths of operating-state n-channel transistors in the operating-state of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a product of the number of the operating-state gate circuits and a sum of both a first averaged value of gate capacitances of the operating-state p-channel transistors and a second averaged value of interconnection capacitances between the operating-state p-channel transistors and the first power is defined to be a model first load capacity; and a half of a product of the number of the operating-state gate circuits and a sum of both a first averaged value of gate capacitances of the operating-state n-channel transistors and a second averaged value of interconnection capacitances between the operating-state n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0157] It is also preferable that in the first sequential processes, informations about gate widths of all p-channel transistors of the constituting gate circuits and an information about operational rate of operating-state p-channel transistors in the operating-state are utilized to decide a gate width of a model p-channel transistor; informations about gate widths of all n-channel transistors of the constituting gate circuits and an information about operational rate of operating-state n-channel transistors in the operating-state are utilized to decide a gate width of a model n-channel transistor; informations about gate capacities of the all p-channel transistors of the constituting gate circuits and informations about interconnection capacitances between the all p-channel transistors and a first power and informations about the operational rate are utilized to decide a model first load capacity; and informations about gate capacities of the all n-channel transistors of the constituting gate circuits and informations about interconnection capacitances between the all n-channel transistors and a second power and informations about the operational rate are utilized to decide a model second load capacity, whereby the logic gate circuit part comprising at least a pair of p-channel and n-channel transistors and at least a pair of first and second load capacities is designed.  
     [0158] It is also preferable that a product of the number of the all gate circuits, an average operational rate of the gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a product of the number of the all gate circuits, an average operational rate of the gate circuits, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a product of the number of the all gate circuits, an average operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a product of the number of the all gate circuits, an average operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0159] It is also preferable that a half of a product of the number of the all gate circuits, an average operational rate of the gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a product of the number of the all gate circuits, an average operational rate of the gate circuits, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a product of the number of the all gate circuits, an average operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a half of a product of the number of the all gate circuits, an average operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0160] It is also preferable that a product of the number of the all gate circuits, a maximum operational rate of the gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0161] It is also preferable that a half of a product of the number of the all gate circuits, a maximum operational rate of the gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a half of a product of the number of the all gate circuits, the maximum operational rate of the gate circuits, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0162] It is also preferable that in the first sequential processes, informations about gate widths of all p-channel transistors of the constituting gate circuits and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide a gate width of a model p-channel transistor; informations about gate widths of all n-channel transistors of the constituting gate circuits and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide a gate width of a model n-channel transistor; informations about gate capacities of the all p-channel transistors of the constituting gate circuits and informations about interconnection capacitances between the all p-channel transistors and a first power and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide a model first load capacity; and informations about gate capacities of the all n-channel transistors of the constituting gate circuits and informations about interconnection capacitances between the all n-channel transistors and a second power and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide a model second load capacity, whereby the logic gate circuit part comprising at least a pair of p-channel and n-channel transistors and at least a pair of first and second load capacities is designed.  
     [0163] It is also preferable that a product of the number of the all gate circuits, and a power current ratio of an averaged current value of the basic gate circuits to an averaged current value of the constituting gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a product of the number of the all gate circuits, the power current ratio, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a product of the number of the all gate circuits, the power current ratio, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a product of the number of the all gate circuits, the power current ratio, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising a single pair of p-channel and n-channel transistors and a single pair of first and second load capacities is designed.  
     [0164] It is also preferable that a half of a product of the number of the all gate circuits, and a power current ratio of an averaged current value of the basic gate circuits to an averaged current value of the constituting gate circuits, and an averaged value of gate widths of the all p-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model p-channel transistor; a half of a product of the number of the all gate circuits, the power current ratio, and an averaged value of gate widths of all n-channel transistors in the all of the constituting gate circuits is defined to be a gate width of a model n-channel transistor; a half of a product of the number of the all gate circuits, the power current ratio, and a sum of both a first averaged value of gate capacitances of the all p-channel transistors and a second averaged value of interconnection capacitances between the all p-channel transistors and the first power is defined to be a model first load capacity; and a half of a product of the number of the all gate circuits, the power current ratio, and a sum of both a first averaged value of gate capacitances of the all n-channel transistors and a second averaged value of interconnection capacitances between the all n-channel transistors and the second power is defined to be a model second load capacity, whereby the logic gate circuit part comprising two pairs of p-channel and n-channel transistors and two pairs of first and second load capacities is designed.  
     [0165] It is also preferable that in the second sequential processes, informations about ON-resistances of non-operating-state transistors in the non-operating-state of the constituting gate circuits are utilized to decide an ON-resistance of an equivalent internal capacity; and informations about gate capacities of the non-operating-state transistors in the non-operating-state of the constituting gate circuits and about interconnection capacitances between the operating-state transistors and a power are utilized to decide the equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0166] It is also preferable that a double of a reciprocal of a sum of reciprocals of ON-resistances of non-operating p-channel transistors in the non-operating state is defined to be an ON-resistance of a third equivalent internal capacity; a double of a reciprocal of a sum of reciprocals of ON-resistances of non-operating n-channel transistors in the non-operating state is defined to be an ON-resistance of a second equivalent internal capacity; an arithmetic mean of a sum of gate capacities of the non-operating p-channel transistors and a sum of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and an arithmetic mean of a sum of gate capacities of the non-operating n-channel transistors and a sum of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0167] It is also preferable that a double of a product of an averaged value of ON-resistances of non-operating p-channel transistors in the non-operating state and a reciprocal of the number of non-operating gate circuits is defined to be an ON-resistance of a third equivalent internal capacity; a double of a product of an averaged value of ON-resistances of non-operating n-channel transistors in the non-operating state and a reciprocal of the number of the non-operating gate circuit is defined to be an ON-resistance of a second equivalent internal capacity; a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating p-channel transistors and an averaged value of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating n-channel transistors and an averaged value of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0168] It is also preferable that in the second sequential processes, informations about an averaged value of ON-resistances of all transistors included in the constituting gate circuits and the number of non-operating gate circuits are utilized to decide an ON-resistance of an equivalent internal capacity; and informations about an averaged value of gate capacities of the non-operating-state transistors in the non-operating-state of the constituting gate circuits, and the number of non-operating gate circuits as well as informations about an averaged value of interconnection capacitances between the operating-state transistors and a power are utilized to decide the equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0169] It is also preferable that the number of non-operating gate circuits in the non-operating state is defined to be a product of a total number of the constituting logic gate included in the semiconductor integrated circuit and a remainder by subtracting an average operational rate from 1; a double of a product of an averaged value of ON-resistances of non-operating p-channel transistors in the non-operating state and a reciprocal of the number of non-operating gate circuits is defined to be an ON-resistance of a third equivalent internal capacity; a double of a product of an averaged value of ON-resistances of non-operating n-channel transistors in the non-operating state and a reciprocal of the number of the non-operating gate circuit is defined to be an ON-resistance of a second equivalent internal capacity; a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating p-channel transistors and an averaged value of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating n-channel transistors and an averaged value of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0170] It is also preferable that the number of non-operating gate circuits in the non-operating state is defined to be a product of a total number of the constituting logic gate included in the semiconductor integrated circuit and a remainder by subtracting a maximum operational rate from 1; a double of a product of an averaged value of ON-resistances of non-operating p-channel transistors in the non-operating state and a reciprocal of the number of non-operating gate circuits is defined to be an ON-resistance of a third equivalent internal capacity; a double of a product of an averaged value of ON-resistances of non-operating n-channel transistors in the non-operating state and a reciprocal of the number of the non-operating gate circuit is defined to be an ON-resistance of a second equivalent internal capacity; a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating p-channel transistors and an averaged value of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating n-channel transistors and an averaged value of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0171] It is also preferable that informations about an averaged value of ON-resistances of all transistors included in the constituting gate circuits and informations about currents of basic gate circuits and the constituting gate circuits are utilized to decide an ON-resistance of an equivalent internal capacity; and informations about an averaged value of gate capacities of the non-operating-state transistors in the non-operating-state of the constituting gate circuits, and informations about currents of basic gate circuits and the constituting gate circuits as well as informations about an averaged value of interconnection capacitances between the operating-state transistors and a power are utilized to decide the equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0172] It is also preferable that the number of non-operating gate circuits in the non-operating state is defined to be a product of the total number of the constituting gate circuits included in the semiconductor integrated circuit and a power current ratio which is defined to be a ratio of an averaged current value of all of basic gate circuits to an averaged current value of all of the constituting gate circuits; a double of a product of an averaged value of ON-resistances of non-operating p-channel transistors in the non-operating state and a reciprocal of the number of non-operating gate circuits is defined to be an ON-resistance of a third equivalent internal capacity; a double of a product of an averaged value of ON-resistances of non-operating n-channel transistors in the non-operating state and a reciprocal of the number of the non-operating gate circuit is defined to be an ON-resistance of a second equivalent internal capacity; a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating p-channel transistors and an averaged value of interconnection capacities between the non-operating p-channel transistors and a first power is defined to be the second equivalent internal capacity; and a product of the number of the non-operating gate circuit and an arithmetic mean of an averaged value of gate capacities of the non-operating n-channel transistors and an averaged value of interconnection capacities between the non-operating n-channel transistors and a second power is defined to be the third equivalent internal capacity, whereby the equivalent internal capacitive part comprising at least the equivalent internal capacity is designed.  
     [0173] It is also preferable that the equivalent internal capacitive part is placed between the logic gate circuit part and a power system side.  
     [0174] It is also preferable that the power model is deigned for simulation to a current distribution over a circuit board on which the semiconductor integrated circuit is mounted.  
     [0175] It is also preferable that the power model is deigned for an electromagnetic interference simulation to an electromagnetic field distribution over a circuit board on which the semiconductor integrated circuit is mounted.  
     [0176] It is also preferable that the computer program further includes a first simulation program for analysis to circuits.  
     [0177] It is also preferable that the first simulation program is to obtain a current distribution over a circuit board on which the semiconductor integrated circuit is mounted.  
     [0178] It is also preferable that the computer program further more includes a second simulation program for analysis to electromagnetic field to obtain a distribution of electromagnetic field over the circuit board on which the semiconductor integrated circuit is mounted.  
     [0179] The fifth present invention provides a simulator for simulating an electromagnetic interference. The simulator comprises : a circuit analyzing simulator being accessible to a first storage medium for receiving a power model for a semiconductor integrated circuit, and also being connected to a second storage medium for receiving informations about a circuit board on which the semiconductor integrated circuit is mounted, so that the circuit analyzing simulator analyzes the power model to obtain a current distribution over a circuit board on which the semiconductor integrated circuit is mounted; an electromagnetic field analyzing simulator being accessible to the circuit analyzing simulator for receiving the current distribution, so that the electromagnetic field analyzing simulator analyzes an electromagnetic field distribution over the circuit board on which the semiconductor integrated circuit is mounted, wherein the power model comprises a logic gate circuit part representing an operating part of the semiconductor integrated circuit and an equivalent internal capacitive part representing a non-operating part of the semiconductor integrated circuit.  
     [0180] It is also preferable that the power model is independently provided for each of plural power systems which are independent from each other and included in the semiconductor integrated circuit.  
     [0181] It is also preferable that internal circuit configurations of the semiconductor integrated circuit are divided into plural blocks on the basis of arrangement informations, and the power model is provided for each of the plural blocks.  
     [0182] It is also preferable that internal circuit configurations of the semiconductor integrated circuit are divided into plural groups, each of the plural groups comprises a same timing group which includes logic gate circuits having individual signal transmission delay times fallen in a group-belonging predetermined time range which belongs to each of the plural groups, and the power model is provided for each of the plural groups.  
     [0183] It is also preferable that the power model further comprises a signal source connected to the logic gate circuit part for supplying a frequency-fixed signal to the logic gate circuit part, so that the logic gate circuit part represents operating state parts of the semiconductor integrated circuit in accordance with the frequency-fixed signal, and the equivalent internal capacitive part represents non-operating state parts of the semiconductor integrated circuit.  
     [0184] It is also preferable that the equivalent internal capacitive part further represents operating-irrelevant fixed parts of the semiconductor integrated circuit.  
     [0185] It is also preferable that the logic gate circuit part is connected between first and second powers, and the equivalent internal capacitive part is also connected between the first and second powers.  
     [0186] It is also preferable that the logic gate circuit part further comprises a single pair of an inverter circuit and a load capacitive element, and the inverter circuit is connected between the first and second powers and the load capacitive element is also connected between the first and second powers, and the load capacitive element is placed between the inverter circuit and the equivalent internal capacitive part.  
     [0187] It is also preferable that the load capacitive element comprises a series connection of a first load capacitance and a second load capacitance between the first and second powers, and an intermediate point between the first and second load capacitances is connected to an output terminal of the inverter circuit.  
     [0188] It is also preferable that the equivalent internal capacitive part further comprises at least an equivalent internal capacitive element connected between the first and second powers.  
     [0189] It is also preferable that a plurality of the equivalent internal capacitive element is connected between the first and second powers, and the equivalent internal capacitive element comprises a series connection of a capacitance and a resistance between the first and second powers.  
     [0190] It is also preferable that the inverter circuit comprises a series connection of a p-channel MOS field effect transistor and an n-channel MOS field effect transistor, and gate electrodes of the p-channel and n-channel MOS field effect transistors are connected to a clock signal source for applying a clock signal to the gate electrodes of the p-channel and n-channel MOS field effect transistors.  
     [0191] It is also preferable that the logic gate circuit part further comprises plural pairs of an inverter circuit and a load capacitive element, and the inverter circuit is connected between the first and second powers and the load capacitive element is also connected between the first and second powers, and in each pair, the load capacitive element is placed closer to the equivalent internal capacitive part than the inverter circuit.  
     [0192] It is also preferable that the load capacitive element comprises a series connection of a first load capacitance and a second load capacitance between the first and second powers, and an intermediate point between the first and second load capacitances is connected to an output terminal of the inverter circuit.  
     [0193] It is also preferable that the equivalent internal capacitive part further comprises at least an equivalent internal capacitive element connected between the first and second powers.  
     [0194] It is also preferable that a plurality of the equivalent internal capacitive element is connected between the first and second powers, and the equivalent internal capacitive element comprises a series connection of a capacitance and a resistance between the first and second powers.  
     [0195] It is also preferable that the inverter circuit comprises a series connection of a p-channel MOS field effect transistor and an n-channel MOS field effect transistor, and gate electrodes of the p-channel and n-channel MOS field effect transistors are connected to a clock signal source for applying a clock signal to the gate electrodes of the p-channel and n-channel MOS field effect transistors.  
     [0196] It is also preferable that the equivalent internal capacitive part is placed between the logic gate circuit part and a power system side.  
     [0197] Accordingly, the present invention also provides a novel power model for an electromagnetic interference simulation to a semiconductor integrated circuit free from the above problems.  
     [0198] The present invention also provides a novel power model for an electromagnetic interference simulation to a semiconductor integrated circuit, wherein the power model allows an extremely accurate electromagnetic interference simulation from a power system of a printed board.  
     [0199] The present invention also provides a novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model makes it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0200] The present invention also provides a novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to allow an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0201] The present invention also provides a novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to make it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0202] The present invention also provides a novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit free from the above problems.  
     [0203] The present invention also provides a novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the method allows an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0204] The present invention also provides a novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the method makes it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0205] The present invention also provides a novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to allow an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0206] The present invention also provides a novel method of designing a power model for an electromagnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to make it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0207] The present invention also provides a novel electro-magnetic interference simulator using a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit free from the above problems.  
     [0208] The present invention also provides a novel electro-magnetic interference simulator using a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the electro-magnetic interference simulator allows an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0209] The present invention also provides a novel electro-magnetic interference simulator using a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the electro-magnetic interference simulator makes it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0210] The present invention also provides a novel electro-magnetic interference simulator using a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to allow an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0211] The present invention also provides a novel electro-magnetic interference simulator using a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to make it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0212] The present invention also provides a novel power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit free from the above problems.  
     [0213] The present invention also provides a novel power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model preparation computer program allows an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0214] The present invention also provides a novel power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model preparation computer program makes it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0215] The present invention also provides a novel power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to allow an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0216] The present invention also provides a novel power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to make it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0217] The present invention also provides a novel storage medium for storing a power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit free from the above problems.  
     [0218] The present invention also provides a novel storage medium for storing a power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model preparation computer program allows an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0219] The present invention also provides a novel storage medium for storing a power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model preparation computer program makes it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0220] The present invention also provides a novel storage medium for storing a power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to allow an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0221] The present invention also provides a novel storage medium for storing a power model preparation computer program for preparing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to make it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0222] The present invention also provides a novel power model design support system for supporting a design for a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit free from the above problems.  
     [0223] The present invention also provides a novel power model design support system for supporting a design for a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model allows an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0224] The present invention also provides a novel power model design support system for supporting a design for a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model makes it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     [0225] The present invention also provides a novel power model design support system for supporting a design for a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to allow an extremely accurate electromagnetic interference simulation from a power system of a printed board.  
     [0226] The present invention also provides a novel power model design support system for supporting a design for a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit, wherein the power model is designed on the basis of all informations about connections and interconnections of the circuits to make it easy to conduct an extremely accurate electro-magnetic interference simulation from a power system of a printed board.  
     PREFERRED EMBODIMENTS  
     First Embodiment  
     [0227] A first embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 3 is a circuit diagram illustrative of a first novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a first embodiment in accordance with the present invention. The first novel power model  18  has a first power  7  and a second power  8 . The first novel power model  18  also has the following elements. An operational signal source (a clock signal source)  1  is provided which is connected to the second power  8 . An inverter circuit  2  is also provided which is connected between the first and second powers  7  and  8 . The inverter circuit  2  is further connected to the operational signal source (a clock signal source)  1  for receiving a lock signal from the operational signal source (a clock signal source)  1 . First and second load capacities  5  and  6  are also provided which are connected in series between the first and second powers  7  and  8 , wherein the first load capacity  5  is directly connected to the first power  7 , whilst the second load capacity  6  is directly connected to the first power  8 . The inverter circuit  2  comprises a series connection of a p-channel MOS field effect transistor  3  and an n-channel MOS field effect transistor  4  between the first and second powers  7  and  8 . A gate of the p-channel MOS field effect transistor  3  is connected to the operational signal source (a clock signal source)  1  for receiving a lock signal from the operational signal source (a clock signal source)  1 . A gate of the n-channel MOS field effect transistor  4  is also connected to the operational signal source (a clock signal source)  1  for receiving a lock signal from the operational signal source (a clock signal source)  1 . The p-channel MOS field effect transistor  3  is connected between the first power  7  and an output terminal  71  of the inverter circuit  2 . The n-channel MOS field effect transistor  4  is connected between the second power  8  and the output terminal  71  of the inverter circuit  2 . The output terminal  71  of the inverter circuit  2  is connected to an intermediate point between the first and second load capacities  5  and  6 . A first equivalent internal capacitive element  9  is provided which is connected between the first and second powers  7  and  8 . The series connection of the first and second load capacities  5  and  6  is placed between the inverter circuit  2  and the first equivalent internal capacitive element  9 . The first equivalent internal capacitive element  9  further comprises a series connection of a first equivalent internal capacity  12  and a first equivalent internal series resistance  13 . The first equivalent internal capacity  12  is directly connected to the first power  7 , whilst the first equivalent internal series resistance  13  is directly connected to the second power  8 . A second equivalent internal capacitive element  10  is provided which is connected between the first and second powers  7  and  8 . The first equivalent internal capacitive element  9  is placed between the series connection of the first and second load capacities  5  and  6  and the second equivalent internal capacitive element  10 . The second equivalent internal capacitive element  10  further comprises a series connection of a second equivalent internal capacity  15  and a second equivalent internal series resistance  14 . The second equivalent internal capacity  15  is directly connected to the second power  8 , whilst the second equivalent internal series resistance  14  is directly connected to the first power  7 . A third equivalent internal capacitive element  11  is provided which is connected between the first and second powers  7  and  8 . The second equivalent internal capacitive element  10  is placed between the first equivalent internal capacitive element  9  and the third equivalent internal capacitive element  11 . The third equivalent internal capacitive element  11  further comprises a series connection of a third equivalent internal capacity  17  and a third equivalent internal series resistance  16 . The third equivalent internal capacity  17  is directly connected to the second power  8 , whilst the third equivalent internal series resistance  16  is directly connected to the first power  7 . An equivalent internal capacitive part comprising the first, second and third equivalent internal capacitive elements  9 ,  10  and  11  is placed between the inverter circuit  2  and the power side having the first and second powers  7  and  8 . The gate circuit comprises the inverter circuit  2  and the series connection of the first and second load capacities  5  and  6 . Namely, the equivalent internal capacitive part is placed between the gate circuit and the power side having the first and second powers  7  and  8 . The operational signal source (a clock signal source)  1  generates a frequency-fixed signal such as a clock signal.  
     [0228] The logic gate circuit having the inverter circuit represents operating state parts of the semiconductor integrated circuit in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part represents non-operating state parts of the semiconductor integrated circuits, wherein the non-operating state parts are in the rest state, even the non-operating state parts are potentially operable in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part also represents an operating-irrelevant fixed part of the semiconductor integrated circuit, wherein the operating-irrelevant fixed part of the semiconductor integrated circuit corresponds to a constant capacitance value, and the operating-irrelevant fixed part of the semiconductor integrated circuit is previously decided in the design process and independent from the operating and non-operating states. The logic gate circuit having the inverter circuit  2  and the first and second load capacitances  5  and  6  corresponds to the operating state parts of the semiconductor integrated circuit. The first equivalent internal capacitive element  9  corresponds to the operating-irrelevant fixed part of the semiconductor integrated circuit. The second and third equivalent internal capacitive elements  10  and  11  correspond to the non-operating state parts of the semiconductor integrated circuit.  
     [0229] The first novel electro-magnetic interference (EMI) simulation power mode is represented in the transistor description format for conducting the simulation to the radiation electro-magnetic field generated on the printed board. This transistor description format large scale integrated circuit power model is largely reduced in the number of transistors constituting this model. The electro-magnetic interference (EMI) simulator utilizes this transistor description format large scale integrated circuit power model to find a power current which flows on an interconnection of a printed board. This transistor description format large scale integrated circuit power model is prepared by extracting operating parts from a net-list for the large scale integrated circuit to reduce the number of transistors constituting this model. Non-operating state parts of the large scale integrated circuit are simplified to be incorporated into the power model. Namely, the transistor description format large scale integrated circuit power model includes the operating state parts extracted from the net-list and the simplified non-operating state parts, so that all of the parts of the large scale integrated circuit are utilized to prepare the transistor description format large scale integrated circuit power model.  
     [0230] The power system of the large scale integrated circuit is modeled into the logic gate part and the equivalent internal capacitive part. As compared to the conventional transistor description format large scale integrated circuit power model, a calculation load to the electro-magnetic interference (EMI) simulator is reduced, thereby making it easy to conduct the power current analysis. The non-operating state parts of the large scale integrated circuit are considered on the electro-magnetic interference (EMI) simulation, whereby the large scale integrated circuit model shows similar operations or behaviors to the actual operations or behaviors of the actual large scale integrated circuit. This makes it possible to find a highly accurate power current of the large scale integrated circuit. Since the confidential detailed informations about the internal circuit configurations of the large scale integrated circuit and the device structures are not included in this transistor description format large scale integrated circuit power model, the maker who manufactures the large scale integrated circuit is likely to show this transistor description format large scale integrated circuit power model to the user with keeping the detailed informations to be confidential.  
     Second Embodiment  
     [0231] A second embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 4 is a circuit diagram illustrative of a second novel power model for an electromagnetic interference simulation to a semiconductor integrated circuit in a second embodiment in accordance with the present invention. The second novel power model  29  has a first power  7  and a second power  8 . The second novel power model  29  also has the following elements. An operational signal source (a clock signal source)  1  is provided which is connected to the second power  8 . A logic gate circuit part comprises two stages. A first stage has a first stage inverter circuit  19  and a first series connection of first and second first-stage load capacities  22  and  23 . The first stage inverter circuit  19  is connected between the first and second powers  7  and  8 . The first stage inverter circuit  19  is further connected to the operational signal source (a clock signal source)  1  for receiving a lock signal from the operational signal source (a clock signal source)  1 . The first and second first-stage load capacities  22  and  23  are connected in series between the first and second powers  7  and  8 , wherein the first first-stage load capacity  22  is directly connected to the first power  7 , whilst the second first-stage load capacity  23  is directly connected to the first power  8 . The first stage inverter circuit  19  comprises a series connection of a p-channel MOS field effect transistor  20  and an n-channel MOS field effect transistor  21  between the first and second powers  7  and  8 . A gate of the p-channel MOS field effect transistor  20  is connected to the operational signal source (a clock signal source)  1  for receiving a lock signal from the operational signal source (a clock signal source)  1 . A gate of the n-channel MOS field effect transistor  21  is also connected to the operational signal source (a clock signal source)  1  for receiving a lock signal from the operational signal source (a clock signal source)  1 . The p-channel MOS field effect transistor  20  is connected between the first power  7  and an output terminal  71  of the first stage inverter circuit  19 . The n-channel MOS field effect transistor  21  is connected between the second power  8  and the output terminal  71  of the first stage inverter circuit  19 . The output terminal  71  of the first stage inverter circuit  19  is connected to an intermediate point between the first and second first-stage load capacities  22  and  23 . A second-stage has a second-stage inverter circuit  24  and a second series connection of first and second second-stage load capacities  27  and  28 . The second-stage inverter circuit  24  is connected between the first and second powers  7  and  8 . The second-stage inverter circuit  24  is further connected to the output terminal  71  of the first-stage inverter circuit  19  for receiving an output signal from the first-stage inverter circuit  19 . The first and second second-stage load capacities  27  and  28  are connected in series between the first and second powers  7  and  8 , wherein the first second-stage load capacity  27  is directly connected to the first power  7 , whilst the second second-stage load capacity  28  is directly connected to the first power  8 . The second-stage inverter circuit  24  comprises a series connection of a p-channel MOS field effect transistor  25  and an n-channel MOS field effect transistor  26  between the first and second powers  7  and  8 . A gate of the p-channel MOS field effect transistor  25  is connected to the output terminal  71  of the first-stage inverter circuit  19  for receiving an output signal from the first-stage inverter circuit  19 . A gate of the n-channel MOS field effect transistor  26  is also connected to the output terminal  71  of the first-stage inverter circuit  19  for receiving an output signal from the first-stage inverter circuit  19 . The p-channel MOS field effect transistor  25  is connected between the first power  7  and an output terminal  72  of the second-stage inverter circuit  24 . The n-channel MOS field effect transistor  26  is connected between the second power  8  and the output terminal  72  of the second-stage inverter circuit  24 . The output terminal  72  of the second-stage inverter circuit  24  is connected to an intermediate point between the first and second second-stage load capacities  27  and  28 . A first equivalent internal capacitive element  9  is provided which is connected between the first and second powers  7  and  8 . The first equivalent internal capacitive element  9  further comprises a series connection of a first equivalent internal capacity  12  and a first equivalent internal series resistance  13 . The first equivalent internal capacity  12  is directly connected to the first power  7 , whilst the first equivalent internal series resistance  13  is directly connected to the second power  8 . A second equivalent internal capacitive element  10  is provided which is connected between the first and second powers  7  and  8 . The first equivalent internal capacitive element  9  is placed between the series connection of the first and second second-stage load capacities  27  and  28  and the second equivalent internal capacitive element  10 . The second equivalent internal capacitive element  10  further comprises a series connection of a second equivalent internal capacity  15  and a second equivalent internal series resistance  14 . The second equivalent internal capacity  15  is directly connected to the second power  8 , whilst the second equivalent internal series resistance  14  is directly connected to the first power  7 . A third equivalent internal capacitive element  11  is provided which is connected between the first and second powers  7  and  8 . The second equivalent internal capacitive element  10  is placed between the first equivalent internal capacitive element  9  and the third equivalent internal capacitive element  11 . The third equivalent internal capacitive element  11  further comprises a series connection of a third equivalent internal capacity  17  and a third equivalent internal series resistance  16 . The third equivalent internal capacity  17  is directly connected to the second power  8 , whilst the third equivalent internal series resistance  16  is directly connected to the first power  7 . An equivalent internal capacitive part comprising the first, second and third equivalent internal capacitive elements  9 ,  10  and  11  is placed between the second-stage inverter circuit  24  and the power side having the first and second powers  7  and  8 . The gate circuit comprises the first-stage inverter circuit  19  and the first series connection of the first and second first-stage load capacities  22  and  23 , and further the second-stage inverter circuit  24  and the second series connection of the first and second second-stage load capacities  27  and  28 . Namely, the equivalent internal capacitive part is placed between the logic gate circuit and the power side having the first and second powers  7  and  8 . The operational signal source (a clock signal source)  1  generates a frequency-fixed signal such as a clock signal.  
     [0232] The two stage logic gate circuit represents operating state parts of the semiconductor integrated circuit in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part represents non-operating state parts of the semiconductor integrated circuits, wherein the non-operating state parts are in the rest state, even the non-operating state parts are potentially operable in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part also represents an operating-irrelevant fixed part of the semiconductor integrated circuit, wherein the operating-irrelevant fixed part of the semiconductor integrated circuit corresponds to a constant capacitance value, and the operating-irrelevant fixed part of the semiconductor integrated circuit is previously decided in the design process and independent from the operating and non-operating states. The logic gate circuit having the first-stage inverter circuit  19  and the first and second first-stage load capacitances  22  and  23  and also having the second-stage inverter circuit  24  and the first and second second-stage load capacitances  27  and  28  corresponds to the operating state parts of the semiconductor integrated circuit. The first equivalent internal capacitive element  9  corresponds to the operating-irrelevant fixed part of the semiconductor integrated circuit. The second and third equivalent internal capacitive elements  10  and  11  correspond to the non-operating state parts of the semiconductor integrated circuit.  
     [0233] In order to make the second novel power model equivalent in time-mean current to the first novel power model, respective gate electrode widths of the p-channel and n-channel MOS field effect transistors  20 ,  21 ,  25  and  26  of the second novel power model are reduced to one half of respective gate electrode widths of the p-channel and n-channel MOS field effect transistors  3  and  4  of the first power model. Further, respective gate electrode capacitances of the p-channel and n-channel MOS field effect transistors  20 ,  21 ,  25  and  26  of the second novel power model are reduced to one half of respective gate electrode capacitances of the p-channel and n-channel MOS field effect transistors  3  and  4  of the first power model. Further more, respective interconnection capacitances of the second novel power model are reduced to one half of respective interconnection capacitances of the first power model. Moreover, respective ON-resistances of the p-channel and n-channel MOS field effect transistors  20 ,  21 ,  25  and  26  of the second novel power model are increased to two times of respective ON-resistances of the p-channel and n-channel MOS field effect transistors  3  and  4  of the first power model.  
     [0234] The second novel electromagnetic interference (EMI) simulation power mode is represented in the transistor description format for conducting the simulation to the radiation electro-magnetic field generated on the printed board. This transistor description format large scale integrated circuit power model is largely reduced in the number of transistors constituting this model. The electromagnetic interference (EMI) simulator utilizes this transistor description format large scale integrated circuit power model to find a power current which flows on an interconnection of a printed board. This transistor description format large scale integrated circuit power model is prepared by extracting operating parts from a net-list for the large scale integrated circuit to reduce the number of transistors constituting this model. Non-operating state parts of the large scale integrated circuit are simplified to be incorporated into the power model. Namely, the transistor description format large scale integrated circuit power model includes the operating state parts extracted from the net-list and the simplified non-operating state parts, so that all of the parts of the large scale integrated circuit are utilized to prepare the transistor description format large scale integrated circuit power model.  
     [0235] The power system of the large scale integrated circuit is modeled into the logic gate part and the equivalent internal capacitive part. As compared to the conventional transistor description format large scale integrated circuit power model, a calculation load to the electromagnetic interference (EMI) simulator is reduced, thereby making it easy to conduct the power current analysis. The non-operating state parts of the large scale integrated circuit are considered on the electromagnetic interference (EMI) simulation, whereby the large scale integrated circuit model shows similar operations or behaviors to the actual operations or behaviors of the actual large scale integrated circuit. This makes it possible to find a highly accurate power current of the large scale integrated circuit. Since the confidential detailed informations about the internal circuit configurations of the large scale integrated circuit and the device structures are not included in this transistor description format large scale integrated circuit power model, the maker who manufactures the large scale integrated circuit is likely to show this transistor description format large scale integrated circuit power model to the user with keeping the detailed informations to be confidential.  
     Third Embodiment  
     [0236] A third embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 5 is a circuit diagram illustrative of a third novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a third embodiment in accordance with the present invention. The third novel power model  30  has two sets of a power system, for example, a first set of a first power and a second power  33  and  34  and a second set of a third power and a fourth power  35  and  36 , wherein the first set of the first and second powers  33  and  34  is independent from the second set of the third and fourth powers  35  and  36 . In this case, a power model  31  is provided for the first set of the first and second powers  33  and  34  as well as a power model  32  is also provided for the second set of the third and fourth powers  35  and  36 . Each of the power models  31  and  32  may comprise either the above described first or second novel power model described in the above first and second embodiments. Namely, the novel power model in accordance with the present invention is provided for each of the plural power systems which are independent from each other.  
     Fourth Embodiment  
     [0237] A fourth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 6 is a circuit diagram illustrative of a fourth novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a fourth embodiment in accordance with the present invention. The fourth novel power model  30  has first and second powers  7  and  8 . In this embodiment, internal circuit configurations of the semiconductor integrated circuit are divided into plural blocks on the basis of arrangement informations, and the power model  37  is provided for each of the plural blocks. Namely, the plural power models  37  are individually provided for the plural blocks of the semiconductor integrated circuit. Each of the plural power models  37  is connected between the first and second powers  7  and  8 . Namely, the plural power models  37  are connected in parallel to each other between the first and second powers  7  and  8 . Each of the power models  37  may comprise either the above described first or second novel power model described in the above first and second embodiments. Namely, the novel power model in accordance with the present invention is provided for each of the plural blocks which are divided from the internal circuit configurations of the semiconductor integrated circuit on the basis of the arrangement or replacement informations of the circuit elements.  
     Fifth Embodiment  
     [0238] A fifth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 7 is a circuit diagram illustrative of a fifth novel power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a fifth embodiment in accordance with the present invention. The fifth novel power model  30  has first and second powers  7  and  8 . In this embodiment, internal circuit configurations of the semiconductor integrated circuit are divided into plural groups. Each of the plural groups comprises the same timing group which includes logic gate circuits having individual signal transmission delay times fallen in a group-belonging predetermined time range which belongs to each of the plural groups. Namely, the internal circuit configurations of the semiconductor integrated circuit are divided into plural groups on the basis of the signal transmission delay time of the logic gate circuits. The power model is provided for each of the plural groups. Namely, the plural power models  37  are individually provided for the plural blocks of the semiconductor integrated circuit. Each of the plural power models  37  is connected between the first and second powers  7  and  8 . Namely, the plural power models  37  are connected in parallel to each other between the first and second powers  7  and  8 . Each of the power models  37  may comprise either the above described first or second novel power model described in the above first and second embodiments. Namely, the novel power model in accordance with the present invention is provided for each of the plural blocks which are divided from the internal circuit configurations of the semiconductor integrated circuit on the basis of the signal transmission delay time of the logic gate circuits.  
     Sixth Embodiment  
     [0239] A sixth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 8 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into a single gate circuit, wherein the novel processes are involved in a first novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a sixth embodiment in accordance with the present invention. All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0240] In a step S 1 , all of the gate circuits in an operating state in accordance with an operational frequency or a clock frequency are extracted from the data base. In second, third and fourth steps S 2 , S 3  and S 4 , the all of the gate circuits in the operating state are modeled into a single gate circuit in order to prepare the above first power model described in the first embodiment in accordance with the present invention.  
     [0241] Namely, in the second step S 2 , the number “m” of the p-channel MOS field effect transistors in the operating state is confirmed. The sum “WP” of gate widths “WPn” of all of the p-channel MOS field effect transistors in the operating state is calculated. The sum “CP” of gate capacities “CPn” of all of the p-channel MOS field effect transistors in the operating state is calculated. The sum “CL 1 ” of interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors in the operating state is calculated.  
     [0242] In the third step S 3 , the number “m” of the n-channel MOS field effect transistors in the operating state is confirmed. The sum “WN” of gate widths “WNn” of all of the n-channel MOS field effect transistors in the operating state is calculated. The sum “CN” of gate capacities “CNn” of all of the n-channel MOS field effect transistors in the operating state is calculated. The sum “CL 2 ” of interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors in the operating state is calculated.  
     [0243] In the fourth step S 4 , the above logic gate circuit part of the above first novel power model shown in FIG. 3 is prepared. As described above, the logic gate circuit part of the above first novel power model comprises the single inverter circuit  2  and a single pair of the first and second load capacities  5  and  6 . The inverter circuit  2  further comprises a single pair of the p-channel MOS field effect transistor  3  and the n-channel MOS field effect transistor  4 . The sum “WP” is defined to be the gate width of the p-channel MOS field effect transistor  3 . The sum “WN” is defined to be the gate width of the n-channel MOS field effect transistor  4 . The sum (“CP”+“CL 1 ”) is defined to be the first load capacity  5 . The sum (“CN”+“CL 2 ”) is defined to be the second load capacity  6 . As a result, the logic gate circuit part of the first power model of the first embodiment is prepared.  
     Seventh Embodiment  
     [0244] A seventh embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 9 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into two-stage gate circuits, wherein the novel processes are involved in the first novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a seventh embodiment in accordance with the present invention. All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0245] In a step S 26 , all of the gate circuits in an operating state in accordance with an operational frequency or a clock frequency are extracted from the data base. In second, third and fourth steps S 27 , S 28  and S 29 , the all of the gate circuits in the operating state are modeled into two-stage gate circuits in order to prepare the above second power model described in the second embodiment in accordance with the present invention.  
     [0246] Namely, in the second step S 27 , the number “m” of the p-channel MOS field effect transistors in the operating state is confirmed. The sum “WP” of gate widths “WPn” of all of the p-channel MOS field effect transistors in the operating state is calculated. The sum “CP” of gate capacities “CPn” of all of the p-channel MOS field effect transistors in the operating state is calculated. The sum “CL 1 ” of interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors in the operating state is calculated.  
     [0247] In the third step S 28 , the number “m” of the n-channel MOS field effect transistors in the operating state is confirmed. The sum “WN” of gate widths “WNn” of all of the n-channel MOS field effect transistors in the operating state is calculated. The sum “CN” of gate capacities “CNn” of all of the n-channel MOS field effect transistors in the operating state is calculated. The sum “CL 2 ” of interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors in the operating state is calculated.  
     [0248] In the fourth step S 29 , the above logic gate circuit part of the above second novel power model shown in FIG. 4 is prepared. As described above, the logic gate circuit part of the above second novel power model comprises the first and second inverter circuits  19  and  24  and a first pair of the first and second load capacities  22  and  23  and a second pair of the third and fourth load capacities  27  and  28 . The first inverter circuit  19  further comprises a single pair of the p-channel MOS field effect transistor  20  and the n-channel MOS field effect transistor  21 . The second inverter circuit  24  further comprises another single pair of the p-channel MOS field effect transistor  25  and the n-channel MOS field effect transistor  26 . The “WP/2” is defined to be the gate width of each of the p-channel MOS field effect transistors  20  and  25 . The “WN/2” is defined to be the gate width of each of the n-channel MOS field effect transistors  21  and  26 . The (“CP”+“CL 1 ”)/2 is defined to be each of the first and third load capacities  22  and  27 . The (“CN”+“CL 2 ”)/2 is defined to be each of the second and fourth load capacities  23  and  28 . As a result, the logic gate circuit part of the second power model of the second embodiment is prepared.  
     Eighth Embodiment  
     [0249] An eighth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 10 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into a single gate circuit, wherein the novel processes are involved in a second novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in an eighth embodiment in accordance with the present invention. All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0250] In a step S 5 , a total number “NgateOP” of the gate circuits in an operating state in accordance with an operational frequency or a clock frequency is counted from all of the circuit configuration informations stored in the data base. In second, third and fourth steps S 6 , S 7  and S 8 , on the basis of the averaged values of the gate widths and gate capacities of the n-channel and p-channel transistors and the averaged values of the interconnection capacities between the drains and the powers of the n-channel and p-channel transistors, all of the gate circuits in the operating state are modeled into a single gate circuit in order to prepare the above first power model described in the first embodiment in accordance with the present invention.  
     [0251] Namely, in the second step S 6 , the averaged value “WPave” of gate widths “WPn” of all of the p-channel MOS field effect transistors in the operating state is calculated. The averaged value “CPave” of gate capacities “CPn” of all of the p-channel MOS field effect transistors in the operating state is calculated. The averaged value “CL 1 ave” of interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors in the operating state is calculated.  
     [0252] In the third step S 7 , the averaged value “WNave” of gate widths “WNn” of all of the n-channel MOS field effect transistors in the operating state is calculated. The averaged value “CNave” of gate capacities “CNn” of all of the n-channel MOS field effect transistors in the operating state is calculated. The averaged value “CL 2 ave” of interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors in the operating state is calculated.  
     [0253] In the fourth step S 8 , the above logic gate circuit part of the above first novel power model shown in FIG. 3 is prepared. As described above, the logic gate circuit part of the above first novel power model comprises the single inverter circuit  2  and a single pair of the first and second load capacities  5  and  6 . The inverter circuit  2  further comprises a single pair of the p-channel MOS field effect transistor  3  and the n-channel MOS field effect transistor  4 . The product “NgateOP×WPave” of the total number “NgateOP” of the gate circuits in the operating state and the averaged value “WPave” is calculated, so that the product “NgateOP×WPave” is defined to be the gate width of the p-channel MOS field effect transistor  3 . The product “NgateOP×WNave” of the total number “NgateOP” of the gate circuits in the operating state and the averaged value “WNave” is calculated, so that the product “NgateOP×WNave” is defined to be the gate width of the n-channel MOS field effect transistor  4 . The product “NgateOP×(“CPave”+“CL 1 ave”)” of total number “NgateOP” of the gate circuits in the operating state and the averaged value (“CPave”+“CL 1 ave”) is calculated, so that the product “NgateOP×(“CPave”+“CL 1 ave”)” is defined to be the first load capacity  5 . The product “NgateOP×(“CNave”+“CL 2 ave”)” of total number “NgateOP” of the gate circuits in the operating state and the averaged value (“CNave”+“CL 2 ave”) is calculated, so that the product “NgateOP×(“CNave”+“CL 2 ave”)” is defined to be the second load capacity  6 . As a result, the logic gate circuit part of the first power model of the first embodiment is prepared.  
     Ninth Embodiment  
     [0254] A ninth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 11 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into two-stage gate circuits, wherein the novel processes are involved in a second novel method of designing a power model for an electromagnetic interference simulation to a semiconductor integrated circuit in a ninth embodiment in accordance with the present invention. All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0255] In a step S 30 , a total number “NgateOP” of the gate circuits in an operating state in accordance with an operational frequency or a clock frequency is counted from all of the circuit configuration informations stored in the data base. In second, third and fourth steps S 31 , S 32  and S 33 , on the basis of the averaged values of the gate widths and gate capacities of the n-channel and p-channel transistors and the averaged values of the interconnection capacities between the drains and the powers of the n-channel and p-channel transistors, all of the gate circuits in the operating state are modeled into two-stage gate circuits in order to prepare the above second power model described in the second embodiment in accordance with the present invention.  
     [0256] Namely, in the second step S 31 , the averaged value “WPave” of gate widths “WPn” of all of the p-channel MOS field effect transistors in the operating state is calculated. The averaged value “CPave” of gate capacities “CPn” of all of the p-channel MOS field effect transistors in the operating state is calculated. The averaged value “CL 1 ave” of interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors in the operating state is calculated.  
     [0257] In the third step S 32 , the averaged value “WNave” of gate widths “WNn” of all of the n-channel MOS field effect transistors in the operating state is calculated. The averaged value “CNave” of gate capacities “CNn” of all of the n-channel MOS field effect transistors in the operating state is calculated. The averaged value “CL 2 ave” of interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors in the operating state is calculated.  
     [0258] In the fourth step S 33 , the above logic gate circuit part of the above second novel power model shown in FIG. 4 is prepared. As described above, the logic gate circuit part of the above second novel power model comprises the first and second inverter circuits  19  and  24  and a first pair of the first and second load capacities  22  and  23  and a second pair of the third and fourth load capacities  27  and  28 . The first inverter circuit  19  further comprises a single pair of the p-channel MOS field effect transistor  20  and the n-channel MOS field effect transistor  21 . The second inverter circuit  24  further comprises another single pair of the p-channel MOS field effect transistor  25  and the n-channel MOS field effect transistor  26 . The product “NgateOP×WPave” of the total number “NgateOP” of the gate circuits in the operating state and the averaged value “WPave” is calculated, so that a half “(NgateOP×WPave)/2” of the product “NgateOP×WPave” is defined to be the gate width of each of the p-channel MOS field effect transistors  20  and  25 . The product “NgateOP×WNave” of the total number “NgateOP” of the gate circuits in the operating state and the averaged value “WNave” is calculated, so that a half “(NgateOP×WNave)/2” of the product “NgateOP×WNave” is defined to be the gate width of each of the n-channel MOS field effect transistors  21  and  26 . The product “NgateOP×(“CPave”+“CL 1 ave”)” of total number “NgateOP” of the gate circuits in the operating state and the averaged value (“CPave”+“CL 1 ave”) is calculated, so that a half “{NgateOP×(“CPave”+“CL 1 ave”)}/2” of the product “NgateOP×(“CPave”+“CL 1 ave”)” is defined to be each of the first and third load capacities  22  and  27 . The product “NgateOP×(“CNave”+“CL 2 ave”)” of total number “NgateOP” of the gate circuits in the operating state and the averaged value (“CNave”+“CL 2 ave”) is calculated, so that a half “{NgateOP×(“CNave”+“CL 2 ave”)}/2” of the product “NgateOP×(“CNave”+“CL 2 ave”)” is defined to be each of the second and fourth load capacities  23  and  28 . As a result, the logic gate circuit part of the second power model of the second embodiment is prepared.  
     Tenth Embodiment  
     [0259] A tenth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 12 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into a single gate circuit, wherein the novel processes are involved in a third novel method of designing a power model for an electromagnetic interference simulation to a semiconductor integrated circuit in a tenth embodiment in accordance with the present invention. All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0260] In a step S 9 , a total number “Ngate” of the all gate circuits included in the semiconductor integrated circuit is counted from all of the circuit configuration informations stored in the data base. In second, third, fourth and fifth steps S 10 , S 11 , S 12  and S 13 , on the basis of the averaged values of the gate widths and gate capacities of the n-channel and p-channel transistors and the averaged values of the interconnection capacities between the drains and the powers of the n-channel and p-channel transistors as well as an average operational rate, all of the gate circuits in the operating state are modeled into a single gate circuit in order to prepare the above first power model described in the first embodiment in accordance with the present invention.  
     [0261] Namely, in the second step S 10 , an average operational rate “ROPave” of the gate circuits is calculated, wherein the average operational rate is defined to be the averaged value of the rate of the operating gate circuits in the operating state in accordance with an operational frequency or a clock frequency to the total gate circuits included in the semiconductor integrated circuit.  
     [0262] In the third step S 11 , the averaged value “WPave” of gate widths “WPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CPave” of gate capacities “CPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CL 1 ave” of interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0263] In the fourth step S 12 , the averaged value “WNave” of gate widths “WNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CNave” of gate capacities “CNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CL 2 ave” of interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0264] In the fifth step S 13 , the above logic gate circuit part of the above first novel power model shown in FIG. 3 is prepared. As described above, the logic gate circuit part of the above first novel power model comprises the single inverter circuit  2  and a single pair of the first and second load capacities  5  and  6 . The inverter circuit  2  further comprises a single pair of the p-channel MOS field effect transistor  3  and the n-channel MOS field effect transistor  4 . The product “Ngate×ROPave×WPave” of the total number “Ngate” of the all gate circuits, and the average operational rate “ROPave”, and the averaged value “WPave” is calculated, so that the product “Ngate×ROPave×WPave” is defined to be the gate width of the p-channel MOS field effect transistor  3 . The product “Ngate×ROPave×WNave” of the total number “Ngate” of the all gate circuits, and the average operational rate “ROPave”, and the averaged value “WNave” is calculated, so that the product “Ngate×ROPave×WNave” is defined to be the gate width of the n-channel MOS field effect transistor  4 . The product “Ngate×ROPave×(“CPave”+“CL 1 ave”)” of total number “Ngate” of the all gate circuits, and the average operational rate “ROPave”, and the averaged value (“CPave”+“CL 1 ave”) is calculated, so that the product “Ngate×ROPave×(“CPave”+“CL 1 ave”)” is defined to be the first load capacity  5 . The product “Ngate×ROPave×(“CNave”+“CL 2 ave”)” of total number “Ngate” of the all gate circuits, and the average operational rate “ROPave”, and the averaged value (“CNave”+“CL 2 ave”) is calculated, so that the product “Ngate×ROPave×(“CNave”+“CL 2 ave”)” is defined to be the second load capacity  6 . As a result, the logic gate circuit part of the first power model of the first embodiment is prepared.  
     Eleventh Embodiment  
     [0265] An eleventh embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 13 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into two-stage gate circuits, wherein the novel processes are involved in a third novel method of designing a power model for an electromagnetic interference simulation to a semiconductor integrated circuit in an eleventh embodiment in accordance with the present invention. All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0266] In a step S 34 , a total number “Ngate” of the all gate circuits included in the semiconductor integrated circuit is counted from all of the circuit configuration informations stored in the data base. In second, third, fourth and fifth steps S 35 , S 36 , S 37  and S 38 , on the basis of the averaged values of the gate widths and gate capacities of the n-channel and p-channel transistors and the averaged values of the interconnection capacities between the drains and the powers of the n-channel and p-channel transistors as well as an average operational rate, all of the gate circuits in the operating state are modeled into two stage gate circuits in order to prepare the above second power model described in the second embodiment in accordance with the present invention.  
     [0267] Namely, in the second step S 35 , an average operational rate “ROPave” of the gate circuits is calculated, wherein the average operational rate is defined to be the averaged value of the rate of the operating gate circuits in the operating state in accordance with an operational frequency or a clock frequency to the total gate circuits included in the semiconductor integrated circuit.  
     [0268] In the third step S 36 , the averaged value “WPave” of gate widths “VVPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CPave” of gate capacities “CPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CL 1 ave” of interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0269] In the fourth step S 37 , the averaged value “WNave” of gate widths “WNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CNave” of gate capacities “CNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CL 2 ave” of interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0270] In the fifth step S 38 , the above logic gate circuit part of the above second novel power model shown in FIG. 4 is prepared. As described above, the logic gate circuit part of the above second novel power model comprises the first and second inverter circuits  19  and  24  and a first pair of the first and second load capacities  22  and  23  and a second pair of the third and fourth load capacities  27  and  28 . The first inverter circuit  19  further comprises a single pair of the p-channel MOS field effect transistor  20  and the n-channel MOS field effect transistor  21 . The second inverter circuit  24  further comprises another single pair of the p-channel MOS field effect transistor  25  and the n-channel MOS field effect transistor  26 . The product “Ngate×ROPave×WPave” of the total number “Ngate” of the all gate circuits, and the average operational rate “ROPave”, and the averaged value “WPave” is calculated, so that a half “{Ngate×ROPave×WPave}/2” of the product “Ngate×ROPave×WPave” is defined to be the gate width of each of the p-channel MOS field effect transistors  20  and  25 . The product “Ngate×ROPave×WNave” of the total number “Ngate” of the all gate circuits, and the average operational rate “ROPave”, and the averaged value “WNave” is calculated, so that a half “{Ngate×ROPave×WNave}/2” of the product “Ngate×ROPave×WNave” is defined to be the gate width of each of the n-channel MOS field effect transistors  21  and  26 . The product “Ngate×ROPave×(“CPave”+“CL 1 ave”)” of total number “Ngate” of the all gate circuits, and the average operational rate “ROPave”, and the averaged value (“CPave”+“CL 1 ave”) is calculated, so that a half“{Ngate×ROPave×(“CPave”+“CL 1 ave”)}/2” of the product “Ngate×ROPave×(“CPave”+“CL 1 ave”)” is defined to be each of the first and third load capacities  22  and  27 . The product “Ngate×ROPave×(“CNave”+“CL 2 ave”)” of total number “Ngate” of the all gate circuits in the operating state, and the average operational rate “ROPave”, and the averaged value (“CNave”+“CL 2 ave”) is calculated, so that a half “{Ngate×ROPave×(“CNave”+“CL 2 ave”)}/2” of the product “Ngate×ROPave×(“CNave”+“CL 2 ave”)” is defined to be each of the second and fourth load capacities  23  and  28 . As a result, the logic gate circuit part of the second power model of the second embodiment is prepared.  
     Twelfth Embodiment  
     [0271] A twelfth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 14 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into a single gate circuit, wherein the novel processes are involved in a fourth novel method of designing a power model for an electromagnetic interference simulation to a semiconductor integrated circuit in a twelfth embodiment in accordance with the present invention. All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0272] In a step S 14 , a total number “Ngate” of the all gate circuits included in the semiconductor integrated circuit is counted from all of the circuit configuration informations stored in the data base. In second, third, fourth and fifth steps S 15 , S 16 , S 17  and S 18 , on the basis of the averaged values of the gate widths and gate capacities of the n-channel and p-channel transistors and the averaged values of the interconnection capacities between the drains and the powers of the n-channel and p-channel transistors as well as a maximum operational rate, all of the gate circuits in the operating state are modeled into a single gate circuit in order to prepare the above first power model described in the first embodiment in accordance with the present invention.  
     [0273] Namely, in the second step S 15 , a maximum operational rate “ROPmax” of the gate circuits is calculated, wherein the maximum operational rate is defined to be the maximum value of the rate of the operating gate circuits in the operating state in accordance with an operational frequency or a clock frequency to the total gate circuits included in the semiconductor integrated circuit.  
     [0274] In the third step S 16 , the averaged value “WPave” of gate widths “WPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CPave” of gate capacities “CPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CL 1 ave” of interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0275] In the fourth step S 17 , the averaged value “WNave” of gate widths “WNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CNave” of gate capacities “CNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CL 2 ave” of interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0276] In the fifth step S 18 , the above logic gate circuit part of the above first novel power model shown in FIG. 3 is prepared. As described above, the logic gate circuit part of the above first novel power model comprises the single inverter circuit  2  and a single pair of the first and second load capacities  5  and  6 . The inverter circuit  2  further comprises a single pair of the p-channel MOS field effect transistor  3  and the n-channel MOS field effect transistor  4 . The product “Ngate×ROPmax×WPave” of the total number “Ngate” of the all gate circuits, and the maximum operational rate “ROPmax”, and the averaged value “WPave” is calculated, so that the product “Ngate×ROPmax×WPave” is defined to be the gate width of the p-channel MOS field effect transistor  3 . The product “Ngate×ROPmax×WNave” of the total number “Ngate” of the all gate circuits in the operating state, and the maximum operational rate “ROPmax”, and the averaged value “WNave” is calculated, so that the product “Ngate×ROPmax×WNave” is defined to be the gate width of the n-channel MOS field effect transistor  4 . The product “Ngate×ROPmax×(“CPave”+“CL 1 ave”)” of total number “Ngate” of the all gate circuits, and the maximum operational rate “ROPmax”, and the averaged value (“CPave”+“CL 1 ave”) is calculated, so that the product “Ngate×ROPmax×(“CPave”+“CL 1 ave”)” is defined to be the first load capacity  5 . The product “Ngate×ROPmax×(“CNave”+“CL 2 ave”)” of total number “Ngate” of the all gate circuits, and the maximum operational rate “ROPmax”, and the averaged value (“CNave”+“CL 2 ave”) is calculated, so that the product “Ngate×ROPmax×(“CNave”+“CL 2 ave”)” is defined to be the second load capacity  6 . As a result, the logic gate circuit part of the first power model of the first embodiment is prepared.  
     Thirteenth Embodiment  
     [0277] A thirteenth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 15 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into two-stage gate circuits, wherein the novel processes are involved in a fourth novel method of designing a power model for an electromagnetic interference simulation to a semiconductor integrated circuit in a thirteenth embodiment in accordance with the present invention. All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0278] In a step S 39 , a total number “Ngate” of the all gate circuits included in the semiconductor integrated circuit is counted from all of the circuit configuration informations stored in the data base. In second, third, fourth and fifth steps S 40 , S 41 , S 42  and S 43 , on the basis of the averaged values of the gate widths and gate capacities of the n-channel and p-channel transistors and the averaged values of the interconnection capacities between the drains and the powers of the n-channel and p-channel transistors as well as a maximum operational rate, all of the gate circuits in the operating state are modeled into two stage gate circuits in order to prepare the above second power model described in the second embodiment in accordance with the present invention.  
     [0279] Namely, in the second step S 40 , a maximum operational rate “ROPmax” of the gate circuits is calculated, wherein the maximum operational rate is defined to be the maximum value of the rate of the operating gate circuits in the operating state in accordance with an operational frequency or a clock frequency to the total gate circuits included in the semiconductor integrated circuit.  
     [0280] In the third step S 41 , the averaged value “WPave” of gate widths “WPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CPave” of gate capacities “CPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CL 1 ave” of interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0281] In the fourth step S 42 , the averaged value “WNave” of gate widths “WNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CNave” of gate capacities “CNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CL 2 ave” of interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0282] In the fifth step S 43 , the above logic gate circuit part of the above second novel power model shown in FIG. 4 is prepared. As described above, the logic gate circuit part of the above second novel power model comprises the first and second inverter circuits  19  and  24  and a first pair of the first and second load capacities  22  and  23  and a second pair of the third and fourth load capacities  27  and  28 . The first inverter circuit  19  further comprises a single pair of the p-channel MOS field effect transistor  20  and the n-channel MOS field effect transistor  21 . The second inverter circuit  24  further comprises another single pair of the p-channel MOS field effect transistor  25  and the n-channel MOS field effect transistor  26 . The product “Ngate×ROPmax×WPave” of the total number “Ngate” of the all gate circuits, and the maximum operational rate “ROPmax”, and the averaged value “WPave” is calculated, so that a half “{Ngate×ROPmax×WPave}/2” of the product “Ngate×ROPmax×WPave” is defined to be the gate width of each of the p-channel MOS field effect transistors  20  and  25 . The product “Ngate×ROPmax×WNave” of the total number “Ngate” of the all gate circuits, and the maximum operational rate “ROPmax”, and the averaged value “WNave” is calculated, so that a half “{Ngate×ROPmax×WNave}/2” of the product “Ngate×ROPmax×WNave” is defined to be the gate width of each of the n-channel MOS field effect transistors  21  and  26 . The product “Ngate×ROPmax×(“CPave”+“CL 1 ave”)” of total number “Ngate” of the all gate circuits, and the maximum operational rate “ROPmax”, and the averaged value (“CPave”+“CL 1 ave”) is calculated, so that a half “{Ngate×ROPmax×(“CPave”+“CL 1 ave”)}/2” of the product “Ngate×ROPmax×(“CPave”+“CL 1 ave”)” is defined to be each of the first and third load capacities  22  and  27 . The product “Ngate×ROPmax×(“CNave”+“CL 2 ave”)” of total number “Ngate” of the all gate circuits, and the maximum operational rate “ROPmax”, and the averaged value (“CNave”+“CL 2 ave”) is calculated, so that a half “{Ngate×ROPmax×(“CNave”+“CL 2 ave”)}/2” of the product “Ngate×ROPmax×(“CNave”+“CL 2 ave”)” is defined to be each of the second and fourth load capacities  23  and  28 . As a result, the logic gate circuit part of the second power model of the second embodiment is prepared.  
     Fourteenth Embodiment  
     [0283] A fourteenth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 16 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into a single gate circuit, wherein the novel processes are involved in a fifth novel method of designing a power model for an electromagnetic interference simulation to a semiconductor integrated circuit in a fourteenth embodiment in accordance with the present invention. All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0284] In a step S 19 , a total number “Ngate” of the gate circuits in an operating state in accordance with an operational frequency or a clock frequency is counted from all of the circuit configuration informations stored in the data base. In second, third, fourth, fifth, sixth and seventh steps S 20 , S 21 , S 22 , S 23 , S 24  and S 25 , on the basis of the averaged values of the gate widths and gate capacities of the n-channel and p-channel transistors and the averaged values of the interconnection capacities between the drains and the powers of the n-channel and p-channel transistors as well as an averaged current value of the entire circuit configuration of the semiconductor integrated circuit and further an averaged current value of a basic gate circuit prepared from the transistors and capacities having the above averaged values, all of the gate circuits in the operating state are modeled into a single gate circuit in order to prepare the above first power model described in the first embodiment in accordance with the present invention.  
     [0285] Namely, in the second step S 20 , an average current value “Iave” of entire circuit configurations of the semiconductor integrated circuits is calculated from all of the circuit configuration informations of the semiconductor integrated circuit stored in the data base.  
     [0286] In the third step S 21 , the averaged value “WPave” of gate widths “WPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CPave” of gate capacities “CPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CL 1 ave” of interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0287] In the fourth step S 22 , the averaged value “WNave” of gate widths “WNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CNave” of gate capacities “CNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CL 2 ave” of interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0288] In the fifth step S 23 , basic gate circuits are prepared in respective correspondence with the actual gate circuits included in the semiconductor integrated circuits, wherein informations about the actual gate circuits are stored in the data base. The corresponding basic gate circuit is identical with the actual gate circuit in the circuit configurations, for example, the circuit elements and the number of the circuit elements and placements and interconnection relationships between the circuit elements. However, the corresponding basic gate circuit is different from the actual gate circuit in the followings. All of the constitutional p-channel MOS field effect transistors of the basic gate circuit have the above averaged gate width “WPave”. All of the constitutional p-channel MOS field effect transistors of the basic gate circuit have the above averaged gate capacity “CPave”. All of the constitutional n-channel MOS field effect transistors of the basic gate circuit has the above averaged gate width “WNave”. All of the constitutional n-channel MOS field effect transistors of the basic gate circuit have the above averaged gate capacity “CNave”. An average current value “IPR 1 ave” of the above basic gate circuits in correspondence with the actual gate circuits included in the semiconductor device is calculated.  
     [0289] In the sixth step S 24 , a power current ratio “CI” is calculated, wherein the power current ratio “CI” is defined to be “IPR 1 ave/Iave”, or the ratio of the average current value “IPRIave” of the above basic gate circuits to the average current value “Iave” of the above actual gate circuits.  
     [0290] In the seventh step S 25 , the above logic gate circuit part of the above first novel power model shown in FIG. 3 is prepared. As described above, the logic gate circuit part of the above first novel power model comprises the single inverter circuit  2  and a single pair of the first and second load capacities  5  and  6 . The inverter circuit  2  further comprises a single pair of the p-channel MOS field effect transistor  3  and the n-channel MOS field effect transistor  4 . The product “Ngate×CI×WPave” of the total number “Ngate” of the all gate circuits, and the power current ratio “CI”, and the averaged value “WPave” is calculated, so that the product “Ngate×ROPmax×WPave” is defined to be the gate width of the p-channel MOS field effect transistor  3 . The product “Ngate×CI×WNave” of the total number “Ngate” of the all gate circuits, and the power current ratio “CI”, and the averaged value “WNave” is calculated, so that the product “Ngate×CI×WNave” is defined to be the gate width of the n-channel MOS field effect transistor  4 . The product “Ngate×CI×(“CPave”+“CL 1 ave”)” of total number “Ngate” of the all gate circuits, and the power current ratio “CI”, and the averaged value (“CPave”+“CL 1 ave”) is calculated, so that the product “Ngate×CI×(“CPave”+“CL 1 ave”)” is defined to be the first load capacity  5 . The product “Ngate×CI×(“CNave”+“CL 2 ave”)” of total number “Ngate” of the all gate circuits, and the power current ratio “CI”, and the averaged value (“CNave”+“CL 2 ave”) is calculated, so that the product “Ngate×CI×(“CNave”+“CL 2 ave”)” is defined to be the second load capacity  6 . As a result, the logic gate circuit part of the first power model of the first embodiment is prepared.  
     Fifteenth Embodiment  
     [0291] A fifteenth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 17 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into two stage gate circuits, wherein the novel processes are involved in a fifth novel method of designing a power model for an electromagnetic interference simulation to a semiconductor integrated circuit in a fifteenth embodiment in accordance with the present invention. All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0292] In a step S 44 , a total number “Ngate” of the all gate circuits included in the semiconductor integrated circuit is counted from all of the circuit configuration informations stored in the data base. In second, third, fourth, fifth, sixth and seventh steps S 45 , S 46 , S 47 , S 48 , S 49  and S 50 , on the basis of the averaged values of the gate widths and gate capacities of the n-channel and p-channel transistors and the averaged values of the interconnection capacities between the drains and the powers of the n-channel and p-channel transistors as well as an averaged current value of the entire circuit configuration of the semiconductor integrated circuit and further an averaged current value of a basic gate circuit prepared from the transistors and capacities having the above averaged values, all of the gate circuits in the operating state are modeled into a single gate circuit in order to prepare the above second power model described in the second embodiment in accordance with the present invention.  
     [0293] Namely, in the second step S 45 , an average current value “ 1 ave” of entire circuit configurations of the semiconductor integrated circuits is calculated from all of the circuit configuration informations of the semiconductor integrated circuit stored in the data base.  
     [0294] In the third step S 46 , the averaged value “WPave” of gate widths “WPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CPave” of gate capacities “CPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CL 1 ave” of interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0295] In the fourth step S 47 , the averaged value “WNave” of gate widths “WNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CNave” of gate capacities “CNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The averaged value “CL 2 ave” of interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0296] In the fifth step S 48 , basic gate circuits are prepared in respective correspondence with the actual gate circuits included in the semiconductor integrated circuits, wherein informations about the actual gate circuits are stored in the data base. The corresponding basic gate circuit is identical with the actual gate circuit in the circuit configurations, for example, the circuit elements and the number of the circuit elements and placements and interconnection relationships between the circuit elements. However, the corresponding basic gate circuit is different from the actual gate circuit in the followings. All of the constitutional p-channel MOS field effect transistors of the basic gate circuit have the above averaged gate width “WPave”. All of the constitutional p-channel MOS field effect transistors of the basic gate circuit have the above averaged gate capacity “CPave”. All of the constitutional n-channel MOS field effect transistors of the basic gate circuit has the above averaged gate width “WNave”. All of the constitutional n-channel MOS field effect transistors of the basic gate circuit have the above averaged gate capacity “CNave”. An average current value “IPR 1 ave” of the above basic gate circuits in correspondence with the actual gate circuits included in the semiconductor device is calculated.  
     [0297] In the sixth step S 49 , a power current ratio “CI” is calculated, wherein the power current ratio “CI” is defined to be “IPR 1 ave/ 1 ave”, or the ratio of the average current value “IPR 1 ave” of the above basic gate circuits to the average current value “ 1 ave” of the above actual gate circuits.  
     [0298] In the seventh step S 50 , the above logic gate circuit part of the above second novel power model shown in FIG. 4 is prepared. As described above, the logic gate circuit part of the above second novel power model comprises the first and second inverter circuits  19  and  24  and a first pair of the first and second load capacities  22  and  23  and a second pair of the third and fourth load capacities  27  and  28 . The first inverter circuit  19  further comprises a single pair of the p-channel MOS field effect transistor  20  and the n-channel MOS field effect transistor  21 . The second inverter circuit  24  further comprises another single pair of the p-channel MOS field effect transistor  25  and the n-channel MOS field effect transistor  26 . The product “Ngate×CI×WPave” of the total number “Ngate” of the all gate circuits, and the power current ratio “CI”, and the averaged value “WPave” is calculated, so that a half “{Ngate×CI×WPave}/2” of the product “Ngate×CI×WPave” is defined to be the gate width of each of the p-channel MOS field effect transistors  20  and  25 . The product “Ngate×CI×WNave” of the total number “Ngate” of the all gate circuits, and the power current ratio “CI”, and the averaged value “WNave” is calculated, so that a half “{Ngate×CI×WNave}/2” of the product “Ngate×CI×WNave” is defined to be the gate width of each of the n-channel MOS field effect transistors  21  and  26 . The product “Ngate×CI×(“CPave”+“CL 1 ave”)” of total number “Ngate” of the all gate circuits, and the power current ratio “CI”, and the averaged value (“CPave”+“CL 1 ave”) is calculated, so that a half “{Ngate×CI×(“CPave”+“CL 1 ave”)}/2” of the product “Ngate×CI×(“CPave”+“CL 1 ave”)” is defined to be each of the first and third load capacities  22  and  27 . The product “Ngate×CI×(“CNave”+“CL 2 ave”)” of total number “Ngate” of the all gate circuits, and the power current ratio “CI”, and the averaged value (“CNave”+“CL 2 ave”) is calculated, so that a half “{Ngate×CI×(“CNave”+“CL 2 ave”)}/2” of the product “Ngate×CI×(“CNave”+“CL 2 ave”)” is defined to be each of the second and fourth load capacities  23  and  28 . As a result, the logic gate circuit part of the second power model of the second embodiment is prepared.  
     Sixteenth Embodiment  
     [0299] A sixteenth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 18 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into an equivalent internal capacitive part, wherein the novel processes are involved in the first novel method of designing a power model for an electromagnetic interference simulation to a semiconductor integrated circuit in a sixteenth embodiment in accordance with the present invention.  
     [0300] The above sixth embodiment in accordance with the present invention does provide the logic gate circuit part of the first power model shown in FIG. 3 described in the above first embodiment in accordance with the present invention. Namely, the logic gate circuit part of the first power model shown in FIG. 3 described in the above first embodiment is prepared in accordance with the novel processes shown in FIG. 8 described in the sixth embodiment. The remaining part, for example, the equivalent internal capacitive part of the first power model shown in FIG. 3 described in the above first embodiment is prepared in accordance with novel processes to be hereinafter described in this embodiment. Accordingly, a combination of the above described novel processes of the above sixth embodiment with the hereinafter described novel processes of this embodiment completes the first novel method of designing the first power model shown in FIG. 3 described in the first embodiment.  
     [0301] The above seventh embodiment in accordance with the present invention does provide the logic gate circuit part of the second power model shown in FIG. 4 described in the above second embodiment in accordance with the present invention. Namely, the logic gate circuit part of the second power model shown in FIG. 4 described in the above second embodiment is prepared in accordance with the novel processes shown in FIG. 9 described in the seventh embodiment. The remaining part, for example, the equivalent internal capacitive part of the second power model shown in FIG. 4 described in the above second embodiment is prepared in accordance with novel processes to be hereinafter described in this embodiment. Accordingly, a combination of the above described novel processes of the above seventh embodiment with the hereinafter described novel processes of this embodiment completes the second novel method of designing the second power model shown in FIG. 4 described in the second embodiment.  
     [0302] All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0303] In a step S 51 , all of the gate circuits in a non-operating state in accordance with an operational frequency or a clock frequency are extracted from the data base. In second, third and fourth steps S 52 , S 53  and S 54 , the all of the gate circuits in the non-operating state are modeled into the equivalent internal capacitive part comprising the first, second and third equivalent internal capacities  9 ,  10  and  11  shown in FIGS. 3 and 4 in the first and second embodiments in order to prepare the above first and second power models described in the first and second embodiments in accordance with the present invention.  
     [0304] Namely, in the second step S 52 , the number “k” of the p-channel MOS field effect transistors in the non-operating state is confirmed. The reciprocal of the sum of the individual reciprocals of the ON-resistances “RONPn” of all of the p-channel MOS field effect transistors in the non-operating state is calculated. The sum “CP” of gate capacities “CPn” of all of the p-channel MOS field effect transistors in the non-operating state is calculated. The sum “CL 1 ” of interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors in the non-operating state is calculated.  
     [0305] In the third step S 53 , the number “k” of the n-channel MOS field effect transistors in the non-operating state is confirmed. The reciprocal of the sum of the individual reciprocals of the ON-resistances “RONNn” of all of the n-channel MOS field effect transistors in the non-operating state is calculated. The sum “CN” of gate capacities “CNn” of all of the n-channel MOS field effect transistors in the non-operating state is calculated. The sum “CL 2 ” of interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors in the non-operating state is calculated.  
     [0306] In the fourth step S 54 , the above equivalent internal capacitive part of each of the above first and second novel power models shown in FIGS. 3 and 4 is prepared. As described above, the above equivalent internal capacitive part of each of the above first and second novel power models comprises the first, second and third equivalent internal capacities  9 ,  10  and  11  shown in FIGS. 3 and 4 described in the first and second embodiments. As described in the first and second embodiments, the logic gate circuit having the inverter circuit represents operating state parts of the semiconductor integrated circuit in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part represents non-operating state parts of the semiconductor integrated circuits, wherein the non-operating state parts are in the rest state, even the non-operating state parts are potentially operable in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part also represents an operating-irrelevant fixed part of the semiconductor integrated circuit, wherein the operating-irrelevant fixed part of the semiconductor integrated circuit corresponds to a constant capacitance value, and the operating-irrelevant fixed part of the semiconductor integrated circuit is previously decided in the design process and independent from the operating and non-operating states. The first equivalent internal capacitive element  9  corresponds to the operating-irrelevant fixed part of the semiconductor integrated circuit. The second and third equivalent internal capacitive elements  10  and  11  correspond to the non-operating state parts of the semiconductor integrated circuit. The product “2RONPn” of “2” and the ON-resistances “RONPn” of all of the p-channel MOS field effect transistors in the non-operating state is defined to be the series resistance of the third equivalent internal capacitive element  11 . The product “2RONNn” of “2” and the ON-resistances “RONNn” of all of the n-channel MOS field effect transistors in the non-operating state is defined to be the series resistance of the second equivalent internal capacitive element  10 . The arithmetic mean “(CP+CL 1 )/2” of the sum “CP” of gate capacities “CPn” of all of the p-channel MOS field effect transistors in the non-operating state and the sum “CL 1 ” of interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors in the non-operating state is defined to be the second equivalent internal capacity  10 . The arithmetic mean “(CN+CL 2 )/2” of the sum “CN” of gate capacities “CNn” of all of the n-channel MOS field effect transistors in the non-operating state and the sum “CL 2 ” of interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors in the non-operating state is defined to be the third equivalent internal capacity  11 . The first equivalent internal capacity  9  is the operating-irrelevant fixed part of the semiconductor integrated circuit and is previously decided in the design process and independent from the operating and non-operating states, for which reason the first equivalent internal capacity  9  is not modeled. As a result, the equivalent internal capacitive part of each of the first and second power models of the first and second embodiments is prepared.  
     Seventh Embodiment  
     [0307] A seventeenth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 19 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into an equivalent internal capacitive part, wherein the novel processes are involved in the second novel method of designing a power model for an electromagnetic interference simulation to a semiconductor integrated circuit in a seventeenth embodiment in accordance with the present invention.  
     [0308] The above eighth embodiment in accordance with the present invention does provide the logic gate circuit part of the first power model shown in FIG. 3 described in the above first embodiment in accordance with the present invention. Namely, the logic gate circuit part of the first power model shown in FIG. 3 described in the above first embodiment is prepared in accordance with the novel processes shown in FIG. 10 described in the eighth embodiment. The remaining part, for example, the equivalent internal capacitive part of the first power model shown in FIG. 3 described in the above first embodiment is prepared in accordance with novel processes to be hereinafter described in this embodiment. Accordingly, a combination of the above described novel processes of the above eighth embodiment with the hereinafter described novel processes of this embodiment completes the second novel method of designing the first power model shown in FIG. 3 described in the first embodiment.  
     [0309] The above ninth embodiment in accordance with the present invention does provide the logic gate circuit part of the second power model shown in FIG. 4 described in the above second embodiment in accordance with the present invention. Namely, the logic gate circuit part of the second power model shown in FIG. 4 described in the above second embodiment is prepared in accordance with the novel processes shown in FIG. 11 described in the ninth embodiment. The remaining part, for example, the equivalent internal capacitive part of the second power model shown in FIG. 4 described in the above second embodiment is prepared in accordance with novel processes to be hereinafter described in this embodiment. Accordingly, a combination of the above described novel processes of the above ninth embodiment with the hereinafter described novel processes of this embodiment completes the second novel method of designing the second power model shown in FIG. 4 described in the second embodiment.  
     [0310] All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0311] In a step S 55 , all of the gate circuits in a non-operating state in accordance with an operational frequency or a clock frequency are extracted from the data base and a total number “NgateNOP” of the gate circuits in the non-operating state is counted. In second, third and fourth steps S 56 , S 57  and S 58 , the all of the gate circuits in the non-operating state are modeled into the equivalent internal capacitive part comprising the first, second and third equivalent internal capacities  9 ,  10  and  11  shown in FIGS. 3 and 4 in the first and second embodiments in order to prepare the above first and second power models described in the first and second embodiments in accordance with the present invention.  
     [0312] Namely, in the second step S 56 , the ON-resistance average value “RONPave” of the ON-resistances “RONPn” of all of the p-channel MOS field effect transistors in the non-operating state is calculated. The gate capacity average value “CPave” of gate capacities “CPn” of all of the p-channel MOS field effect transistors in the non-operating state is calculated. The interconnection capacity average value “CL 1 ave” of the interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors in the non-operating state is calculated.  
     [0313] In the third step S 57 , the ON-resistance average value “RONNn” of the ON-resistances “RONNn” of all of the n-channel MOS field effect transistors in the non-operating state is calculated. The gate capacity average value “CNave” of gate capacities “CNn” of all of the n-channel MOS field effect transistors in the non-operating state is calculated. The interconnection capacity average value “CL 2 ave” of the interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors in the non-operating state is calculated.  
     [0314] In the fourth step S 58 , the above equivalent internal capacitive part of each of the above first and second novel power models shown in FIGS. 3 and 4 is prepared. As described above, the above equivalent internal capacitive part of each of the above first and second novel power models comprises the first, second and third equivalent internal capacities  9 ,  10  and  11  shown in FIGS. 3 and 4 described in the first and second embodiments. As described in the first and second embodiments, the logic gate circuit having the inverter circuit represents operating state parts of the semiconductor integrated circuit in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part represents non-operating state parts of the semiconductor integrated circuits, wherein the non-operating state parts are in the rest state, even the non-operating state parts are potentially operable in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part also represents an operating-irrelevant fixed part of the semiconductor integrated circuit, wherein the operating-irrelevant fixed part of the semiconductor integrated circuit corresponds to a constant capacitance value, and the operating-irrelevant fixed part of the semiconductor integrated circuit is previously decided in the design process and independent from the operating and non-operating states. The first equivalent internal capacitive element  9  corresponds to the operating-irrelevant fixed part of the semiconductor integrated circuit. The second and third equivalent internal capacitive elements  10  and  11  correspond to the non-operating state parts of the semiconductor integrated circuit. The “2RONPave/NgateNOP” is defined to be the series resistance of the third equivalent internal capacitive element  11 . The “2RONNave/NgateNOP” is defined to be the series resistance of the second equivalent internal capacitive element  10 . The product “NgateNOP×(CPave+CL 1 ave)/2” of the total number “NgateNOP” of the logic gate circuits in the non-operating state and the arithmetic mean “(CPave+CL 1 ave)/2” of the average gate capacities “CPave” of all of the p-channel MOS field effect transistors in the non-operating state and the average interconnection capacities “CL 1 ave” between drains and the first power of all of the p-channel MOS field effect transistors in the non-operating state is defined to be the second equivalent internal capacity  10 . The product “NgateNOP×(CNave+CL 2 ave)/2” of the total number “NgateNOP” of the logic gate circuits in the non-operating state and the arithmetic mean “(CNave+CL 2 ave)/2” of the average gate capacities “CNave” of all of the n-channel MOS field effect transistors in the non-operating state and the average interconnection capacities “CL 2 ave” between drains and the second power of all of the n-channel MOS field effect transistors in the non-operating state is defined to be the third equivalent internal capacity  11 . The first equivalent internal capacity  9  is the operating-irrelevant fixed part of the semiconductor integrated circuit and is previously decided in the design process and independent from the operating and non-operating states, for which reason the first equivalent internal capacity  9  is not modeled. As a result, the equivalent internal capacitive part of each of the first and second power models of the first and second embodiments is prepared.  
     Eighteenth Embodiment  
     [0315] An eighteenth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 20 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into an equivalent internal capacitive part, wherein the novel processes are involved in the third novel method of designing a power model for an electromagnetic interference simulation to a semiconductor integrated circuit in an eighteenth embodiment in accordance with the present invention.  
     [0316] The above tenth embodiment in accordance with the present invention does provide the logic gate circuit part of the first power model shown in FIG. 3 described in the above first embodiment in accordance with the present invention. Namely, the logic gate circuit part of the first power model shown in FIG. 3 described in the above first embodiment is prepared in accordance with the novel processes shown in FIG. 12 described in the tenth embodiment. The remaining part, for example, the equivalent internal capacitive part of the first power model shown in FIG. 3 described in the above first embodiment is prepared in accordance with novel processes to be hereinafter described in this embodiment. Accordingly, a combination of the above described novel processes of the above tenth embodiment with the hereinafter described novel processes of this embodiment completes the third novel method of designing the first power model shown in FIG. 3 described in the first embodiment.  
     [0317] The above eleventh embodiment in accordance with the present invention does provide the logic gate circuit part of the second power model shown in FIG. 4 described in the above second embodiment in accordance with the present invention. Namely, the logic gate circuit part of the second power model shown in FIG. 4 described in the above second embodiment is prepared in accordance with the novel processes shown in FIG. 13 described in the eleventh embodiment. The remaining part, for example, the equivalent internal capacitive part of the second power model shown in FIG. 4 described in the above second embodiment is prepared in accordance with novel processes to be hereinafter described in this embodiment. Accordingly, a combination of the above described novel processes of the above eleventh embodiment with the hereinafter described novel processes of this embodiment completes the third novel method of designing the second power model shown in FIG. 4 described in the second embodiment.  
     [0318] All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0319] In a step S 59 , all of the gate circuits both in the operating and non-operating states in accordance with an operational frequency or a clock frequency are extracted from the data base and a total number “Ngate” of the gate circuits included in the semiconductor integrated circuit is counted. In second, third, fourth, fifth and sixth steps S 60 , S 61 , S 62 , S 63  and S 64 , the all of the gate circuits in the non-operating state are modeled into the equivalent internal capacitive part comprising the first, second and third equivalent internal capacities  9 ,  10  and  11  shown in FIGS. 3 and 4 in the first and second embodiments in order to prepare the above first and second power models described in the first and second embodiments in accordance with the present invention.  
     [0320] Namely, in the second step S 60 , an average operational rate “ROPave” of the gate circuits is calculated, wherein the average operational rate is defined to be the averaged value of the rate of the operating gate circuits in the operating state in accordance with an operational frequency or a clock frequency to the total gate circuits included in the semiconductor integrated circuit.  
     [0321] In the third step S 61 , a total number “NgateNOP” of the gate circuits in the non-operating state is calculated, wherein the total number “NgateNOP” of the gate circuits in the non-operating state is defined to be the product “Ngate×(1−ROPave)” of the total number “Ngate” of the gate circuits included in the semiconductor integrated circuit and the value “(1−ROPave)”.  
     [0322] In the fourth step S 62 , the ON-resistance average value “RONPave” of the ON-resistances “RONPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The gate capacity average value “CPave” of gate capacities “CPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The interconnection capacity average value “CL 1 ave” of the interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0323] In the fifth step S 63 , the ON-resistance average value “RONNn” of the ON-resistances “RONNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The gate capacity average value “CNave” of gate capacities “CNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The interconnection capacity average value “CL 2 ave” of the interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0324] In the sixth step S 64 , the above equivalent internal capacitive part of each of the above first and second novel power models shown in FIGS. 3 and 4 is prepared. As described above, the above equivalent internal capacitive part of each of the above first and second novel power models comprises the first, second and third equivalent internal capacities  9 ,  10  and  11  shown in FIGS. 3 and 4 described in the first and second embodiments. As described in the first and second embodiments, the logic gate circuit having the inverter circuit represents operating state parts of the semiconductor integrated circuit in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part represents non-operating state parts of the semiconductor integrated circuits, wherein the non-operating state parts are in the rest state, even the non-operating state parts are potentially operable in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part also represents an operating-irrelevant fixed part of the semiconductor integrated circuit, wherein the operating-irrelevant fixed part of the semiconductor integrated circuit corresponds to a constant capacitance value, and the operating-irrelevant fixed part of the semiconductor integrated circuit is previously decided in the design process and independent from the operating and non-operating states. The first equivalent internal capacitive element  9  corresponds to the operating-irrelevant fixed part of the semiconductor integrated circuit. The second and third equivalent internal capacitive elements  10  and  11  correspond to the non-operating state parts of the semiconductor integrated circuit. The “2RONPave/NgateNOP” is defined to be the series resistance of the third equivalent internal capacitive element  11 . The “2RONNave/NgateNOP” is defined to be the series resistance of the second equivalent internal capacitive element  10 . The product “NgateNOP×(CPave+CL 1 ave)/2” of the total number “NgateNOP” of the logic gate circuits in the non-operating state and the arithmetic mean “(CPave+CL 1 ave)/2” of the average gate capacities “CPave” of all of the p-channel MOS field effect transistors in the non-operating state and the average interconnection capacities “CL 1 ave” between drains and the first power of all of the p-channel MOS field effect transistors in the non-operating state is defined to be the second equivalent internal capacity  10 . The product “NgateNOP×(CNave+CL 2 ave)/2” of the total number “NgateNOP” of the logic gate circuits in the non-operating state and the arithmetic mean “(CNave+CL 2 ave)/2” of the average gate capacities “CNave” of all of the n-channel MOS field effect transistors in the non-operating state and the average interconnection capacities “CL 2 ave” between drains and the second power of all of the n-channel MOS field effect transistors in the non-operating state is defined to be the third equivalent internal capacity  11 . The first equivalent internal capacity  9  is the operating-irrelevant fixed part of the semiconductor integrated circuit and is previously decided in the design process and independent from the operating and non-operating states, for which reason the first equivalent internal capacity  9  is not modeled. As a result, the equivalent internal capacitive part of each of the first and second power models of the first and second embodiments is prepared.  
     Nineteenth Embodiment  
     [0325] A nineteenth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 21 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into an equivalent internal capacitive part, wherein the novel processes are involved in the fourth novel method of designing a power model for an electro-magnetic interference simulation to a semiconductor integrated circuit in a nineteenth embodiment in accordance with the present invention.  
     [0326] The above twelfth embodiment in accordance with the present invention does provide the logic gate circuit part of the first power model shown in FIG. 3 described in the above first embodiment in accordance with the present invention. Namely, the logic gate circuit part of the first power model shown in FIG. 3 described in the above first embodiment is prepared in accordance with the novel processes shown in FIG. 14 described in the twelfth embodiment. The remaining part, for example, the equivalent internal capacitive part of the first power model shown in FIG. 3 described in the above first embodiment is prepared in accordance with novel processes to be hereinafter described in this embodiment. Accordingly, a combination of the above described novel processes of the above twelfth embodiment with the hereinafter described novel processes of this embodiment completes the fourth novel method of designing the first power model shown in FIG. 3 described in the first embodiment.  
     [0327] The above thirteenth embodiment in accordance with the present invention does provide the logic gate circuit part of the second power model shown in FIG. 4 described in the above second embodiment in accordance with the present invention. Namely, the logic gate circuit part of the second power model shown in FIG. 4 described in the above second embodiment is prepared in accordance with the novel processes shown in FIG. 15 described in the thirteenth embodiment. The remaining part, for example, the equivalent internal capacitive part of the second power model shown in FIG. 4 described in the above second embodiment is prepared in accordance with novel processes to be hereinafter described in this embodiment. Accordingly, a combination of the above described novel processes of the above thirteenth embodiment with the hereinafter described novel processes of this embodiment completes the fourth novel method of designing the second power model shown in FIG. 4 described in the second embodiment.  
     [0328] All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0329] In a step S 65 , all of the gate circuits both in the operating and non-operating states in accordance with an operational frequency or a clock frequency are extracted from the data base and a total number “Ngate” of the gate circuits included in the semiconductor integrated circuit is counted. In second, third, fourth, fifth and sixth steps S 66 , S 67 , S 68 , S 69  and S 70 , the all of the gate circuits in the non-operating state are modeled into the equivalent internal capacitive part comprising the first, second and third equivalent internal capacities  9 ,  10  and  11  shown in FIGS. 3 and 4 in the first and second embodiments in order to prepare the above first and second power models described in the first and second embodiments in accordance with the present invention.  
     [0330] Namely, in the second step S 66 , an maximum operational rate “ROPmax” of the gate circuits is calculated, wherein the maximum operational rate is defined to be the maximum value of the rate of the operating gate circuits in the operating state in accordance with an operational frequency or a clock frequency to the total gate circuits included in the semiconductor integrated circuit.  
     [0331] In the third step S 67 , a total number “NgateNOP” of the gate circuits in the non-operating state is calculated, wherein the total number “NgateNOP” of the gate circuits in the non-operating state is defined to be the product “Ngate×(1−ROPmax)” of the total number “Ngate” of the gate circuits included in the semiconductor integrated circuit and the value “(1−ROPmax)”.  
     [0332] In the fourth step S 68 , the ON-resistance average value “RONPave” of the ON-resistances “RONPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The gate capacity average value “CPave” of gate capacities “CPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The interconnection capacity average value “CL 1 ave” of the interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0333] In the fifth step S 69 , the ON-resistance average value “RONNn” of the ON-resistances “RONNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The gate capacity average value “CNave” of gate capacities “CNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The interconnection capacity average value “CL 2 ave” of the interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0334] In the sixth step S 70 , the above equivalent internal capacitive part of each of the above first and second novel power models shown in FIGS. 3 and 4 is prepared. As described above, the above equivalent internal capacitive part of each of the above first and second novel power models comprises the first, second and third equivalent internal capacities  9 ,  10  and  11  shown in FIGS. 3 and 4 described in the first and second embodiments. As described in the first and second embodiments, the logic gate circuit having the inverter circuit represents operating state parts of the semiconductor integrated circuit in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part represents non-operating state parts of the semiconductor integrated circuits, wherein the non-operating state parts are in the rest state, even the non-operating state parts are potentially operable in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part also represents an operating-irrelevant fixed part of the semiconductor integrated circuit, wherein the operating-irrelevant fixed part of the semiconductor integrated circuit corresponds to a constant capacitance value, and the operating-irrelevant fixed part of the semiconductor integrated circuit is previously decided in the design process and independent from the operating and non-operating states. The first equivalent internal capacitive element  9  corresponds to the operating-irrelevant fixed part of the semiconductor integrated circuit. The second and third equivalent internal capacitive elements  10  and  11  correspond to the non-operating state parts of the semiconductor integrated circuit. The “2RONPave/NgateNOP” is defined to be the series resistance of the third equivalent internal capacitive element  11 . The “2RONNave/NgateNOP” is defined to be the series resistance of the second equivalent internal capacitive element  10 . The product “NgateNOP×(CPave+CL 1 ave)/2” of the total number “NgateNOP” of the logic gate circuits in the non-operating state and the arithmetic mean “(CPave+CL 1 ave)/2” of the average gate capacities “CPave” of all of the p-channel MOS field effect transistors in the non-operating state and the average interconnection capacities “CL 1 ave” between drains and the first power of all of the p-channel MOS field effect transistors in the non-operating state is defined to be the second equivalent internal capacity  10 . The product “NgateNOP×(CNave+CL 2 ave)/2” of the total number “NgateNOP” of the logic gate circuits in the non-operating state and the arithmetic mean “(CNave+CL 2 ave)/2” of the average gate capacities “CNave” of all of the n-channel MOS field effect transistors in the non-operating state and the average interconnection capacities “CL 2 ave” between drains and the second power of all of the n-channel MOS field effect transistors in the non-operating state is defined to be the third equivalent internal capacity  11 . The first equivalent internal capacity  9  is the operating-irrelevant fixed part of the semiconductor integrated circuit and is previously decided in the design process and independent from the operating and non-operating states, for which reason the first equivalent internal capacity  9  is not modeled. As a result, the equivalent internal capacitive part of each of the first and second power models of the first and second embodiments is prepared.  
     Twentieth Embodiment  
     [0335] A twentieth embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 22 is flow chart illustrative of novel processes for modeling internal circuit configurations of a semiconductor integrated circuit into an equivalent internal capacitive part, wherein the novel processes are involved in the fifth novel method of designing a power model for an electromagnetic interference simulation to a semiconductor integrated circuit in a twentieth embodiment in accordance with the present invention.  
     [0336] The above fourteenth embodiment in accordance with the present invention does provide the logic gate circuit part of the first power model shown in FIG. 3 described in the above first embodiment in accordance with the present invention. Namely, the logic gate circuit part of the first power model shown in FIG. 3 described in the above first embodiment is prepared in accordance with the novel processes shown in FIG. 16 described in the fourteenth embodiment. The remaining part, for example, the equivalent internal capacitive part of the first power model shown in FIG. 3 described in the above first embodiment is prepared in accordance with novel processes to be hereinafter described in this embodiment. Accordingly, a combination of the above described novel processes of the above fourteenth embodiment with the hereinafter described novel processes of this embodiment completes the fifth novel method of designing the first power model shown in FIG. 3 described in the first embodiment.  
     [0337] The above fifteenth embodiment in accordance with the present invention does provide the logic gate circuit part of the second power model shown in FIG. 4 described in the above second embodiment in accordance with the present invention. Namely, the logic gate circuit part of the second power model shown in FIG. 4 described in the above second embodiment is prepared in accordance with the novel processes shown in FIG. 17 described in the fifteenth embodiment. The remaining part, for example, the equivalent internal capacitive part of the second power model shown in FIG. 4 described in the above second embodiment is prepared in accordance with novel processes to be hereinafter described in this embodiment. Accordingly, a combination of the above described novel processes of the above fifteenth embodiment with the hereinafter described novel processes of this embodiment completes the fifth novel method of designing the second power model shown in FIG. 4 described in the second embodiment.  
     [0338] All of the circuit configuration informations of the semiconductor integrated circuit are stored in a data base or a net list.  
     [0339] In a step S 71 , all of the gate circuits both in the operating and non-operating states in accordance with an operational frequency or a clock frequency are extracted from the data base and a total number “Ngate” of the gate circuits included in the semiconductor integrated circuit is counted. In second, third, fourth, fifth and sixth steps S 72 , S 73 , S 74 , S 75  and S 76 , the all of the gate circuits in the non-operating state are modeled into the equivalent internal capacitive part comprising the first, second and third equivalent internal capacities  9 ,  10  and  11  shown in FIGS. 3 and 4 in the first and second embodiments in order to prepare the above first and second power models described in the first and second embodiments in accordance with the present invention.  
     [0340] Namely, in the second step S 72 , an average current value “Iave” of entire circuit configurations of the semiconductor integrated circuits is calculated from all of the circuit configuration informations of the semiconductor integrated circuit stored in the data base.  
     [0341] In the third step S 73 , a gate width average value “WPave” of the gate widths of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The ON-resistance average value “RONPave” of the ON-resistances “RONPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The gate capacity average value “CPave” of gate capacities “CPn” of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The interconnection capacity average value “CL 1 ave” of the interconnection capacities “CL 1 n” between drains and the first power of all of the p-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0342] In the fifth step S 74 , a gate width average value “WNave” of the gate widths of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The ON-resistance average value “RONNn” of the ON-resistances “RONNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The gate capacity average value “CNave” of gate capacities “CNn” of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated. The interconnection capacity average value “CL 2 ave” of the interconnection capacities “CL 2 n” between drains and the second power of all of the n-channel MOS field effect transistors included in the semiconductor integrated circuit is calculated.  
     [0343] In the fifth step S 75 , basic gate circuits are prepared in respective correspondence with the actual gate circuits included in the semiconductor integrated circuits, wherein informations about the actual gate circuits are stored in the data base. The corresponding basic gate circuit is identical with the actual gate circuit in the circuit configurations, for example, the circuit elements and the number of the circuit elements and placements and interconnection relationships between the circuit elements. However, the corresponding basic gate circuit is different from the actual gate circuit in the followings. All of the constitutional p-channel MOS field effect transistors of the basic gate circuit have the above averaged gate width “WPave”. All of the constitutional p-channel MOS field effect transistors of the basic gate circuit have the above averaged gate capacity “CPave”. All of the constitutional n-channel MOS field effect transistors of the basic gate circuit has the above averaged gate width “WNave”. All of the constitutional n-channel MOS field effect transistors of the basic gate circuit have the above averaged gate capacity “CNave”. An average current value “IPR 1 ave” of the above basic gate circuits in correspondence with the actual gate circuits included in the semiconductor device is calculated.  
     [0344] In the sixth step S 76 , a power current ratio “CI” is calculated, wherein the power current ratio is defined to be a ratio of the above averaged current value “IPR 1 ave” of all of the basic gate circuits to an averaged current value “ 1 ave” of all of the constituting gate circuits. A total number “NgateNOP” of the gate circuits in the non-operating state is calculated, wherein the total number “NgateNOP” of the gate circuits in the non-operating state is defined to be the product “Ngate×(1−IPRIave/Iave)” of the total number “Ngate” of the gate circuits included in the semiconductor integrated circuit and the power current ratio “IPR 1 ave/ 1 ave”.  
     [0345] In the sixth step S 77 , the above equivalent internal capacitive part of each of the above first and second novel power models shown in FIGS. 3 and 4 is prepared. As described above, the above equivalent internal capacitive part of each of the above first and second novel power models comprises the first, second and third equivalent internal capacities  9 ,  10  and  11  shown in FIGS. 3 and 4 described in the first and second embodiments. As described in the first and second embodiments, the logic gate circuit having the inverter circuit represents operating state parts of the semiconductor integrated circuit in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part represents non-operating state parts of the semiconductor integrated circuits, wherein the non-operating state parts are in the rest state, even the non-operating state parts are potentially operable in accordance with the frequency-fixed signal such as the clock signal. The equivalent internal capacitive part also represents an operating-irrelevant fixed part of the semiconductor integrated circuit, wherein the operating-irrelevant fixed part of the semiconductor integrated circuit corresponds to a constant capacitance value, and the operating-irrelevant fixed part of the semiconductor integrated circuit is previously decided in the design process and independent from the operating and non-operating states. The first equivalent internal capacitive element  9  corresponds to the operating-irrelevant fixed part of the semiconductor integrated circuit. The second and third equivalent internal capacitive elements  10  and  11  correspond to the non-operating state parts of the semiconductor integrated circuit. The “2RONPave/NgateNOP” is defined to be the series resistance of the third equivalent internal capacitive element  11 . The “2RONNave/NgateNOP” is defined to be the series resistance of the second equivalent internal capacitive element  10 . The product “NgateNOP×(CPave+CL 1 ave)/2” of the total number “NgateNOP” of the logic gate circuits in the non-operating state and the arithmetic mean “(CPave+CL 1 ave)/2” of the average gate capacities “CPave” of all of the p-channel MOS field effect transistors in the non-operating state and the average interconnection capacities “CL 1 ave” between drains and the first power of all of the p-channel MOS field effect transistors in the non-operating state is defined to be the second equivalent internal capacity  10 . The product “NgateNOP×(CNave+CL 2 ave)/2” of the total number “NgateNOP” of the logic gate circuits in the non-operating state and the arithmetic mean “(CNave+CL 2 ave)/2” of the average gate capacities “CNave” of all of the n-channel MOS field effect transistors in the non-operating state and the average interconnection capacities “CL 2 ave” between drains and the second power of all of the n-channel MOS field effect transistors in the non-operating state is defined to be the third equivalent internal capacity  11 . The first equivalent internal capacity  9  is the operating-irrelevant fixed part of the semiconductor integrated circuit and is previously decided in the design process and independent from the operating and non-operating states, for which reason the first equivalent internal capacity  9  is not modeled. As a result, the equivalent internal capacitive part of each of the first and second power models of the first and second embodiments is prepared.  
     Twenty First Embodiment  
     [0346] A twenty first embodiment according to the present invention will be described in detail with reference to the drawings. FIG. 23 is a block diagram illustrative of a support system for designing a power model in a twenty first embodiment according to the present invention. The support system is to realize the above described first and second novel power models of the first and second embodiments in accordance with the above described first, second, third, fourth and fifth novel power model design methods of the above sixth through twentieth embodiments.  
     [0347] The support system has the following elements. A data base  63  is provided for storing informations of internal circuit configurations of the semiconductor integrated circuit, and if any the circuit board on which the semiconductor integrated circuit is mounted. A storage medium  67  is also provided for storing informations  68  about power model circuit elements and interconnections between the circuit elements of the power model as well as for storing a computer program  69  for designing the power model. A processor  64  is provided which is connected to the data base  63  and the storage medium  65  for executing the computer program  69  to prepare the power model. An output device  70  is provided which is connected to the processor  64  for outputting the power model prepared by the processor  64 . The processor  64  further comprises a central processing unit  65  and a memory  66  connected to the central processing unit  65 . The central processing unit  65  is connected to the data base  63  for receiving the circuit informations stored therein. The central processing unit  65  is also connected to the storage medium  67  for receiving both the informations  68  about the power model circuit elements and interconnections between the circuit elements of the power model as well as the computer program  69  for designing the power model. The central processing unit  65  executes the computer program  69  to prepare the power model. The central processing unit  65  is also connected to the output device  70  for enabling the output device  70  to output the power model. The power model may be either the first or second novel power models shown in FIGS. 3 and 4. The computer program  69  accords to the above described first, second, third, fourth and fifth novel power model design methods of the above sixth through twentieth embodiments. The storage medium  67  may be realized by any available mediums such as a magnetic disk, a semiconductor memory, and a CD-ROM. The data base  63  stores all of the informations about the semiconductor integrated circuit. All of the necessary informations for the novel power model are obtained from the output device  70 . The computer program  69  includes both the first program for designing the logic gate circuit part of the power model and the second program for designing the equivalent internal capacitive part, wherein the logic gate circuit part represents the operating parts of the semiconductor integrated circuits, whilst the equivalent internal capacitive part represents the non-operating parts of the semiconductor integrated circuits. There is no limitation to the sequence in execution of the first and second programs. The first equivalent internal capacity  9  in the first and second power models shown in FIGS. 3 and 4 may be obtained from the informations bout placement of the well regions but not from the circuit informations of the semiconductor integrated circuit. The power model is deigned for the electromagnetic interference simulation to an electromagnetic field distribution over a circuit board on which the semiconductor integrated circuit is mounted. For this reason, a simulation program may be included in the above computer program  69  for designing the power model or may be excluded therefrom so that the simulation program is stored in another storage medium of a simulator separately from the above supporting system. If the above computer program  69  includes the simulation program, then the computer program  69  includes a first simulation program for analysis to circuits to obtain a current distribution over a circuit board on which the semiconductor integrated circuit is mounted. The computer program  69  further includes a second simulation program for analysis to electromagnetic field to obtain a distribution of electromagnetic field over the circuit board on which the semiconductor integrated circuit is mounted.  
     [0348]FIG. 24 is a flow chart illustrative of the electromagnetic interference simulation to the semiconductor integrated circuit by use of a simulator on the basis of the first and second novel power models shown in FIGS. 3 and 4 and prepared by the first, second, third, fourth and fifth design methods executed by the supporting system shown in FIG. 23. The simulator may comprise a circuit analyzing simulator  73  and an electromagnetic field analyzing simulator  75 . The circuit analyzing simulator  73  is accessible to a first storage medium  71  for receiving a power model for a semiconductor integrated circuit, and also being connected to a second storage medium  72  for receiving informations about a circuit board on which the semiconductor integrated circuit is mounted, so that the circuit analyzing simulator  73  analyzes the power model to obtain a current distribution  74  over a circuit board on which the semiconductor integrated circuit is mounted. The electromagnetic field analyzing simulator  75  is accessible to the circuit analyzing simulator  73  for receiving the current distribution  74 , so that the electromagnetic field analyzing simulator  75  analyzes an electromagnetic field distribution  76  over the circuit board on which the semiconductor integrated circuit is mounted. The circuit analyzing simulator  73  may, for example comprise “Simulation Program with Integrated Circuit Emphasis (SPICE)”. The above circuit analyzing simulator  73  and the electromagnetic field analyzing simulator  75  may be realized by a single package software such as “RADIA-WB PACKAGE” which is commercially available from Applied Simulation Technology. This package software has a circuit analyzing tool “ApsimSPICE” which corresponds to the circuit analyzing simulator  73 , and an electromagnetic field analyzing tool “RADIA” which corresponds to the electromagnetic field analyzing simulator  75 .  
     [0349]FIG. 25 is a circuit diagram illustrative of a modeled circuit board connected to the novel power model for the electromagnetic interference simulation in accordance with the present invention. In accordance with the foregoing descriptions, the power model for the semiconductor integrated circuit has been described. Hereinafter, the power model for the circuit board on which the semiconductor integrated circuit will be described. The modeled circuit board has the following circuit elements. A de-coupling capacitor  55  is connected between the first ands second powers. The de-coupling capacitor  55  further comprises a series connection of an equivalent series inductance  56 , an equivalent capacity  57  and an equivalent series resistance  58 . A power model  46  is also connected between the first and second powers  7  and  8 . A first lead frame  47  and a first transmission line  53  are connected between the power model  46  and the first power  7 . The first lead frame  47  further comprises a series connection of a first lead frame inductance  48  and a first lead frame resistance  49 . A second lead frame  50  and a second transmission line  54  are connected between the power model  46  and the second power  8 . The second lead frame  50  further comprises a series connection of a second lead frame inductance  51  and a second lead frame resistance  52 . The de-coupling capacitor  55  contributes to suppress the electromagnetic interference. The above circuit board model allows more accurate electromagnetic interference simulation.  
     [0350]FIG. 26 is a circuit diagram illustrative of a modeled semiconductor integrated circuit for the electromagnetic interference simulation in accordance with the present invention. The modeled semiconductor integrated circuit has the following circuit elements. A power model  46  is also connected between the first and second powers  7  and  8 . A de-coupling capacitor  59  is connected between the first ands second powers  7  and  8 . The de-coupling capacitor  59  further comprises a series connection of an equivalent series inductance  60 , an equivalent capacity  61  and an equivalent series resistance  62 . The de-coupling capacitor  59  contributes to suppress the electromagnetic interference. The above semiconductor integrated circuit model allows more accurate electromagnetic interference simulation.  
     [0351]FIG. 27 is a diagram illustrative of variations in currents over frequency to show frequency spectrums which has been transformed by Fourier-transform from a current waveform which represents variation in current over time at a fixed point of a circuit board, wherein  represents an actually measured value, whilst ◯ represents an analyzed value. The analysis was made by use of the design support system shown in FIG. 23 and the simulator shown in FIG. 24. The actual measurement was made by use of a magnetic probe positioned at the same point as the analysis. From FIG. 27, it is understood that the analyzed values are close to the actually measured value and the above novel power model of the present invention is usable in the light of the accuracy in the analysis.  
     [0352] Whereas modifications of the present invention will be apparent to a person having ordinary skill in the art, to which the invention pertains, it is to be understood that embodiments as shown and described by way of illustrations are by no means intended to be considered in a limiting sense. Accordingly, it is to be intended to cover by claims all modifications which fall within the spirit and scope of the present invention.