Patent Publication Number: US-8988084-B2

Title: Device and method for monitoring at least one energy reserve capacitor in a restraint system

Description:
FIELD OF THE INVENTION 
     The present invention relates to a method and a device for monitoring at least one energy reserve capacitor in a restraint system. 
     BACKGROUND INFORMATION 
     German Patent Application No. 197 15 571 describes, for example, monitoring the capacitance of a capacitor used as an energy reserve for a restraint system. 
     SUMMARY 
     A method and device according to an example embodiment of the present invention for monitoring an energy reserve capacitor may have the advantage that the internal resistance of the energy reserve capacitor is also monitored. Aging of aluminum electrolytic capacitors, which are in most cases used as energy reserve capacitors, is accompanied by a change in capacitance and in internal resistance as well. As the number of firing circuits, which, increasingly frequently, have to be fired in parallel and at high current, increases, existing solutions for energy reserve voltage and vehicle battery voltage become less effective since it is not possible for enough current to be adequately provided over a cable connection of 0.5 to 1 ohm internal resistance without appreciable voltage drop. For that reason, it is becoming increasingly important to monitor the internal resistance of the energy reserve capacitors separately as well as monitoring the capacitance thereof. Only in that way is it possible to ensure in the worst case that simultaneous parallel firing at high firing speed and high firing current is able to take place, especially in the case of firing circuits having a relatively high circuit resistance, for example 6.5 ohm. That also ensures that, when the energy store is used at the same time to supply control units, the high current drain of up to 20 amperes during firing does not cause a temporary drop in the energy reserve voltage to below the reset threshold of the voltage supply, which would result in failure of the entire system in the event of a crash. If a fault, for example an unduly high internal resistance, is detected, it will be indicated so that the control unit with that energy reserve may be replaced, since this is only necessary to ensure reliable operation of a restraint device in the event of it being triggered. 
     In the electronics for restraint systems, especially in the control unit, an energy reserve for which either one or more capacitors are used is currently used for firing the restraint device. Thus, the firing of the restraint device is independent of fluctuations in and the state of the battery voltage in the vehicle. The device and method according to the present invention may be applied both in the case of one energy reserve capacitor and in the case of a plurality of energy reserve capacitors. 
     It may be especially advantageous if the device determines the internal resistance of the energy reserve capacitor by a time sequence of at least one charging operation and an interruption of that operation. It is thereby possible to ascertain defined electrical parameters that are influenced by the internal resistance. Consequently, it is then thereby possible to determine the internal resistance using the microcontroller in the control unit. If a number of charging and discharging operations are used, the measurement is more robust. 
     It may also be advantageous if a voltage converter, a rectifier and a voltage divider are provided for monitoring the internal resistance. The voltage converter serves to charge the at least one energy reserve capacitor, and the rectifier and voltage divider connected downstream of the energy reserve capacitor serve to measure the electrical parameters used to determine the internal resistance of the energy reserve capacitor. The rectifier should be a peak rectifier, while the voltage divider is additionally configured as a low-pass filter. That prevents short-term voltage peaks from having an effect on the measurement. The voltage converter preferably has a regulator for its output voltage in order to keep the output voltage in a defined control band after a charging phase of the energy reserve capacitor. 
     The method for determining the internal resistance of the energy reserve capacitor may proceed as follows: 
     In a first step, the capacitor is charged by the voltage converter to a first voltage value which is above the battery voltage. This is necessary in order for the measurement to be performed above the battery voltage, since it may be that the battery voltage is coupled to the energy reserve capacitor directly as a reserve and thus might falsify the measurement. If, however, the energy reserve capacitor is charged to above the battery voltage, the measurement is independent of the behavior of the battery voltage. To provide defined starting conditions, the converter is switched off and an abrupt drop in voltage occurs across the internal resistance of the electrolytic capacitor. That voltage then, however, falls across another component in the circuit. The capacitor of the peak rectifier, on the one hand, and the voltage divider which is connected downstream of the peak rectifier are used for that purpose. That behavior does not occur instantaneously, however, but occurs with a certain delay, and therefore a certain waiting period is observed until a static value is obtained. That period is generally determined by the decay of energy in the coil of the switching converter, the time constants of the peak rectifier, the measuring low-pass filter and any load currents at the output of the peak rectifier. The value of the voltage that falls across the internal resistance of the energy reserve capacitor at the switch-off time is given by the value of the internal resistance and the charging current at that time, the charging current having been delivered to the capacitor. After that waiting period until a static value has been obtained, the energy reserve capacitor is again charged by the converter. The state of charge of the energy reserve capacitor remains virtually unchanged by the change in the time perspective, whereas the voltage across the energy reserve capacitor pulsates in the time of the switching converter. The voltage ux at the output of the peak rectifier assumes the peak value of the pulsating voltage. The converter is then switched off again until a static value has been obtained. As explained above, the internal resistance of the energy reserve capacitor may be determined from the difference between the charged value and the static, fallen value of the peak rectifier. 
     The period for which the converter is switched off is selected in dependence on the residual coil energy, the time constants of the peak rectifier, the measuring low-pass filter and any load currents at the output of the peak rectifier. The charging period in the second charging operation is selected in such a manner that the capacitance of the peak rectifier is increased to the peak value which is by the second voltage at the internal resistance of the energy reserve capacitor, which is caused by the clocked charging current, plus the voltage at the actual capacitance. The method according to the present invention is preferably carried out at cold start since the vehicle is in its coldest state with regard to the electrolytic capacitor. 
     The voltage converter charges the energy reserve capacitor in a clocked manner. For determining the internal resistance of the energy reserve capacitor a switching converter operation of known pulse train amplitude is required in order to determine the internal resistance of the energy reserve capacitor from the observed voltage difference between peak value, when the converter is active, and fallen value, when the converter is inactive. Switching converter operation may be necessary since the voltage applied to the energy reserve and hence the entire measuring procedure is above the voltage of the vehicle battery. The clocked step-up converter used here determines the peak value of the coil current in the transverse branch of the converter. 
     A development of the present invention provides for a series transistor to be provided in the voltage converter. That series transistor makes it possible to control the passage of the battery voltage to the energy reserve capacitor. This reduces the power loss during measurement, since measuring may be carried out at a lower voltage. Furthermore, by blocking the series transistor during the measurement, it is possible to eliminate the effect of the battery voltage on the measurement. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       Exemplary embodiments of the present invention are shown in the figures, and are described in detail below. 
         FIG. 1  is a first circuit diagram of the device according to an example embodiment of the present invention. 
         FIG. 2  is a voltage-time diagram of the charging and discharging operation of the energy reserve capacitor. 
         FIG. 3  is a flow chart of the method according to an example embodiment of the present invention. 
         FIG. 4  is a block diagram of the device according to an example embodiment of the present invention. 
         FIG. 5  is a second circuit diagram of the device according to an example embodiment of the present invention. 
     
    
    
     DETAILED DESCRIPTION OF EXAMPLE EMBODIMENTS 
     A description is provided below of how, as the internal resistance of the energy reserve capacitor increases, the restraint system reacts correctly by indicating a dangerously high internal resistance when it occurs, in order to obtain replacement of the electronics. The signal may, for example, be given to the driver visually on the instrument panel by a display, an audible indication may be given or it is also possible, in addition, for contact to be made via a transmitting/receiving station, for example a mobile telephone, in order to contact a garage or other service establishment. The latter would then be able to inform the driver that replacement is necessary. 
     In order for the device according to the present invention to be operated or implemented, the following conditions should be met: 
     A clocked step-up converter of fixed or variable switching converter frequency is to be provided. The charging voltage of the energy reserve capacitor is ultimately above the highest airbag system supply voltage. In that way, measurement is carried out in a range that is not subject to interference by other variables. In the following, a converter having a coil is presented. The converter features measurement of the coil current in the transverse branch so as to switch to the longitudinal branch after the maximum permissible coil current has been reached. The maximum coil current in clocked charging operation of the energy reserve should be between 0.4 and 1.2 A. That value range is typical for charging even large energy reserves of up to 20 mF to 33±2 volts in times of &lt;10 seconds in medium-sized to relatively large airbag systems. If that is the case, it is possible for internal resistances of the energy reserve capacitor to be resolved with a resolution of from 32 to 96 mΩ. Larger coil currents with further improved resolution of the measurement of the internal resistance are, of course, also possible. 
     The converter is capable of being switched on and off by a processor or microcontroller of the airbag control unit. A peak rectifier formed by a diode and, for example, a ceramic capacitor is connected downstream of the energy reserve. The diode and the ceramic capacitor do not represent new parts in optimally configured airbag systems but, rather, are already present as a general rule for connecting the final stages of restraint systems to the energy reserve. That is to say, that peak rectifier is present in any case. The voltage of the peak rectifier of the energy reserve capacitor is divided by a voltage divider, which either is arranged discretely between diode and ground or is integrated in an integrated circuit, for example in the final stage IC, and is connected as a low-pass filter. The low-pass filter is either formed by a discrete ceramic element between the two partial resistors and ground, or the low-pass filter is formed by correspondingly connecting an operational amplifier for measuring the divider voltage, for example integrated in the final stage ICs. The voltage of the peak rectifier is furthermore measurable by an analog-digital converter. The analog-digital converter is either a component part of the microcontroller or a component part of a switching converter IC that is in serial or parallel connection with the microcontroller via a digital communication connection, or it is a component part of the final stage IC and is in serial or parallel connection with the microcontroller via a digital communication connection. 
     In  FIG. 4 , an overview of the device according to an example embodiment of the present invention is shown in a block diagram. A voltage converter  400  transforms the battery voltage U Bat  to a higher value with which a downstream energy reserve capacitor ER is charged. That energy reserve capacitor has an internal resistance ESR through which the charging current of the voltage converter  400  passes. Connected downstream of the energy reserve capacitor ER is a rectifier  401 . That rectifier prevents unintentional firing by an unintended positive voltage pulse in the downstream firing device  403  or the terminals of the firing element since, without that rectifier  401 , the firing element would be connected to the energy reserve via the backward diodes of the final stage transistors and would therefore conduct current in the event of a potential difference. Connected in parallel between the rectifier  401  and the firing device  403  is a voltage divider  402  which is also configured as a low-pass filter. The voltage divider  402  is used to measure the internal resistance ESR as described below. The voltage measured at the voltage divider  402  is fed to microcontroller μC, more specifically directly into its analog-digital converter. Depending on the value of the internal resistance ESR of the energy reserve capacitor ER thus determined, microcontroller μC activates an indicator  404  which indicates whether the internal resistance ESR has such a high value that replacement of the airbag control unit in which the energy reserve capacitor ER is situated is necessary. That indicator  404  may be a light on the instrument panel, a display on a screen, a spoken announcement or a message transmitted by radio to a service provider. 
       FIG. 1  shows the device according to an example embodiment of the invention in detail in a circuit diagram. In block  100 , the voltage converter is shown. A coil  117  is arranged outside block  100  since all the components in block  100  are integrated in an IC. It is not possible for coil  117 , which is in the form of a pot coil, to be integrated in the IC. Coil  117  is connected on one side to the battery voltage U Bat , or to the polarity-inversion-protected battery voltage VZP, and on the other side to the anode of a diode  109  and, for example, to the drain of a transistor  118 . The gate of transistor  118  is controlled by a switch control  116 . A first input of a comparator  113  and a resistor  112  are connected to the source of transistor  118 . On the other side, resistor  112  is connected to ground and to the second input of comparator  113 . The cathode of diode  109  is connected on the one hand to resistor  110  and on the other hand, outside IC  100 , to the internal resistance of the electrolytic capacitor ESR and to the anode of diode D of a peak rectifier  101 . Resistor  101  is connected on its other side to a first input of an operational amplifier  114  and to a resistor  111 . Resistor  111  is connected on the other side to ground. Resistors  110  and  111  thereby form a voltage divider. A reference voltage is applied to the second input of operational amplifier  114  so that a comparison of the voltage tapped by voltage divider  110  and  111  and that reference voltage takes place using operational amplifier  114 . The output of operational amplifier  114  goes into a first input of a comparator  115 . A sawtooth signal is applied to the second input of comparator  115 . The output of comparator  115  goes into a first input of switch control  116 . The output of comparator  113  is connected to a second input of switch control  116 . Connected to a third input of switch control  116  is a signal line of microcontroller μC, or rather the control line, which, by virtue of serial or parallel communication between microcontroller and switching converter IC, transmits the logic command switching converter active or inactive to the switch control. 
     Internal resistance ESR is connected on its other side to capacitance ER of the energy reserve capacitor. Capacitance ER is connected on the other side to ground. The internal resistance of the electrolytic capacitor is not an electrical component but a modeling of the ohmic losses. The cathode of diode D is connected on the one hand to capacitance C peak     —     D  and to resistor R 1  and to the parallel circuit composed of transistor  104  and the cathode of diode  106 . Transistor  104  and cathode  106  belong to final stage IC  103  which activates firing pellet  108 , transistor  104  and diode  106  being connected to firing element  108  on their other side. Transistor  104  is integrated in the circuit merely by its source and its drain. It acts here as a high-side switch. For the sake of simplicity, the connection of its gate is not shown here. Firing element  108  is connected on the other side to the low-side of final stage ASIC  103 , more specifically to the drain of a transistor  105  and the cathode of diode  107  which is connected by the anode to ground and the drain of transistor  105 . Resistor R 1  belongs to voltage divider  102 , resistor R 1  being connected on its other side to resistor R 2  and capacitor  109 . Both capacitor  109  and resistor R 2  are connected on the other side to ground. 
     Voltage converter  100  converts battery voltage VZP to a higher value to charge the capacitance ER to a value above the battery voltage. In that operation, voltage converter  100  operates in a clocked state, that is to say, in the charging state energy is built up in the coil by the increasing coil current up to ISp max  in the transverse branch through switching transistor  118  of the converter in order to be dissipated again in the blocking phase of switching transistor  118  as a charging current pulse to the energy reserve capacitor ER. A so-called flyback converter is therefore obtained. 
     The clocking of voltage converter  100  is carried out by oscillator signal OSC which is fed to comparator  115 . The signal is pulse-width modulated by the feedback loop formed by voltage divider  110  and  111  and operational amplifier  114  which compares the voltage tapped by voltage divider  110  and  111  with a reference value REF. Pulse-width modulation is thereby achieved. Feedback via comparator  113  is used to limit the coil current in the charging phase of the flyback converter to a maximum value. Diode  109  serves as a polarity inversion protection. Charging current I SP  accordingly passes on the one hand via internal resistance ESR and capacitor ER and, on the other hand, via diode D, and thus charges the small capacitance C peak     —     D  to a voltage peak which may be tapped via resistor R 1  and resistor R 2 . 
     Resistors R 1  and R 2  and also capacitor  109  and capacitance C peak     —     D  are dimensioned in such a manner that the charging current is fed predominantly to capacitor ER. High-side  104  is blocked and diode  106  is switched in such a manner that it blocks the charging current from converter  100 . If voltage converter  100  is switched off and if U ER &gt;VZP, then, after a very short decay of the coil current, charging current no longer passes into capacitor ER and the voltage drop across internal resistance ESR does not occur. That drop is also exhibited by voltage  201  in  FIG. 2 , section  202  of the downstream peak rectifier. 
     Voltage  201 =ux of the peak rectifier is divided by voltage divider  102  formed by R 1  and R 2  and is filtered by  109  in such a manner that it can be fed to an analog-digital converter of a microcontroller μC for voltage measurement. 
     The microcontroller is able to calculate the internal resistance (ESR) of the energy reserve capacitor from the observed drop in voltage at the peak rectifier and a knowledge of the max coil current if the microcontroller, on the other hand, is capable of influencing the operation of the flyback converter and has exact knowledge of the magnitude of the battery voltage U B , (VZP) and of the energy reserve voltage. 
       FIG. 2  illustrates the measuring method in a voltage-time diagram. Voltage  200 =U ER  (voltage at the energy reserve capacitor including the internal resistance with respect to ground) and  201 =ux (output voltage of the peak rectifier with respect to ground) are plotted on the ordinate and time is plotted on the abscissa. In a first section  203 , voltage converter  400  is switched on by microcontroller μC so that charging of capacitor ER to above battery voltage U B  or VZP takes place. In time section  202 , voltage converter  400  is then switched off by microcontroller μC. Owing to the small voltage level difference and to make rapid time processes clearer, the scale has been enlarged (zoomed) in the voltage and time direction. Since charging current is now no longer passing through resistance ESR, there is no voltage drop across that resistance. That does not, however, occur immediately but occurs with a certain delay owing to the decay of the coil current with regard to 200=U ER  and the additional low-pass filtering in the peak rectifier with regard to 201=ux. A waiting period Toff is therefore observed until a static value is obtained. That value is designated u 2  here with regard to 200=ux. A time of ±2·0.5 ms was estimated to be the time Toff here. 
     There then follows a phase  204  in which the voltage converter is switched on for the purposes of energy reserve ESR measurement. The clocked charging of capacitor ER is now clearly shown. That period in time section  204  is 0.5 ms long here. It has the result that the peak rectifier is charged to the value u 3  while UER exceeds that value only in pulses by a diode voltage and a small increase in the voltage base value of the energy reserve capacitance. In  FIG. 2 , this is  201  and  200 , respectively, in section  204 . 
     Time section  204  is followed by time section  205  in which the voltage converter is switched off once more and the voltage u 5  is obtained at the output of the peak rectifier after a waiting period of 2·0.5 ms after all time constants have decayed to ground. 
     The accordingly linearly divided voltages at the output of voltage divider  102  which are identified by upper-case U (u 2 →U 2 , u 3 →U 3 , u 5 →U 5 ) are passed on to the ADC of the microcontroller for calculation of the internal resistance (ESR) of the energy reserve. 
     The voltage of the energy reserve is first increased by charging to a value that cannot be affected by U Bat  (VZP), for example 23 volts, in order to be independent of the battery. Voltage converter  400  is then switched off and, after a waiting period Toff, the voltage at peak rectifier  401  is measured. The waiting period Toff is so selected that the energy in the converter coil has decayed and the undefined peak voltage of the peak rectifier has fallen to the static voltage UER-UD owing to the defined input current of the connected final stages and/or to the ohmic load of the voltage divider, and 4τ of a downstream low-pass filter have elapsed, τ being the time constant of the low-pass filter. Toff was selected to be, for example, 1 ms, which corresponds, for example, to two real-time frames of the microcontroller. 
     An estimation of Toff is given by Toff≈dt 1 +dt 2 +dt 3 : 
     converter coil Lsp*Isp 2 =C ER *(u ER   2 −u ER0   2 ), from which it follows that du ER =3.1 mV where C ER =2.2 mF, from which it follows that dt 1 =5.7 μs 
     peak rectifier: ESR max *ISP max *C peak     —     D /IL=dt 2 =800 μs 
     low-pass filter (formed by  102  and  109  in  FIG. 1 ): 4τ=dt 3 =100 μs 
     Selected Toff&gt;=dt 1 +dt 2 +dt 3 =905.6 μs, Toff=2*0.5 ms 
     Calculation parameters: IL=1.2 mA for the supply of the final stage IC at ER and the divider, and ESR max =4Ω, Isp max =1.2 A, C peak     —     D =200 nF, u ER0 =18 volts, C ER =2.2 mF, Lsp=220 μH. 
     The voltage loss of the energy reserve in the time Toff due to customary static energy reserve load currents is then considered. 
     For an energy reserve of capacitance C ER , the following voltage change is obtained for a load current IL in the time Toff:
 
 du   ERoff   =IL*Tw/C   ER .
 
     When C ER =2.2 mF, IL=1.2 mA, Tw=1 ms, then
 
 du   ERoff =1.2 mA*1 ms/2.2 mF=0.55 mV.
 
     This shows that, for customary energy reserves of from 2.2 to 20 mF, du ERoff  is negligibly small. 
     The equation for U 2  is given below:
 
 U 2 =Ux ( t=T off)= Ux ( t= 2*500 μs)= R  div*[ u   ER ( t=T off)− U   D ]=1449 mV;  Equ. 1
         calculation parameters:       

     
       
         
           
             
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                     U 
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                 18.2 
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     The converter is then switched on and operated for a time Ton. Ton was selected to be 500 μs here. Ton is selected in such a manner that the energy reserve voltage remains virtually unchanged, but the peak rectifier is increased to the value by an internal resistance of the energy reserve caused voltage drop. 
     The equation for U 3  is given below:
 
 U 3 =Ux ( t=T off+ T on)= Ux (3*500 μs)= R  div*[ u   ER ( t=T off+ T on)+Isp max *ESR− U   D ]  Equ. 2
 
ESR=(U3−U2)/(R div*Isp max ),   Equ. 4
 
     being simplified as follows:
 
 u   ER ( t=T off+ T on)≈ u   ER ( t=T off).
 
     The inaccuracy of that simplification may be improved by the following methods: 
     the further charging of the energy reserve in the time Ton is first estimated
 
 du   ERon ≈[(Isp max /3)*500 μs)]/ C   ERon  
 
where, for example, Isp max =1.2 A, C ERon =2200 μF gives du ERon =90 mV.
 
     That results in an improved determination of the internal resistance ESR. Consequently, Equation 4 is to be modified as follows:
 
ESR=( U 3− d   UERon   −U 1)/( R  div*Isp max )  Equ. 5
 
therein U 1  is unknown.
 
     The measurement is expanded by including the measured value u 5 . 
     After measurement of U 3 , the converter is switched off. The waiting period Toff is again observed until the peak value meter indicates the quasi-static voltage UER-UD again, then measurement is carried out, more specifically of u 5  or U 5 . Equation 5 may thereby be expressed without the unknown as follows:
 
ESR=( U 3−( U 5 −U 1)− U 1)/( R  div*Isp max )=( U 3 −U 5)/( R  div*Isp max )  Equ. 6
 
     The following remain as tolerances for determining the internal resistance
     aa) the tolerance of the voltage measurement, which is substantially provided only by the voltage divider. The reference voltage of the analog-digital converter is not included owing to the rapid measuring sequence if it is sufficiently filtered.   bb) a ±1 bit tolerance of the analog-digital converter corresponds in the case of a 10 bit analog-digital converter having a reference voltage of 3.3 V based on the measurement voltage Ux to a value of 38.76 mV   cc) the tolerance of the maximum coil current Isp max . The latter may simply be kept at ±33% by suitable design of the switching regulator, or may be given maximum accuracy, for example 3%, by levelling, for example via a reference resistor.   

     The peak rectifier formed by diode D and capacitance C peak     —     D  are components for the determination of the internal resistance of the energy reserve by the method described above. The components are, however, generally already a component part of an airbag control unit to enable polarity inversion protection of the firing circuits against the energy reserve in the event of short-circuit to U Bat . 
       FIG. 3  is a flow chart showing the method according to the present invention. In method step  300 , charging is carried out to the above-mentioned value of, for example, U ER =23 volts (≈u ER  if ESR≈0). Selected u ER &gt;U Bmax . 
     At the ADC of the microcontroller, ux attains the value U 1 . In method step  301 , the converter is switched off and the current falls to zero, with the result that the voltage drops to U 2 . In method step  302 , charging operation of ER takes place again, the voltage at peak rectifier  101 , 401  being charged to u 3 , or U 3  at the ADC input, in order for the converter to be switched off again in method step  303 , with the result that once more a drop to U 5  occurs. It is then possible in method step  304  for the internal resistance of the energy reserve capacitor to be determined from the voltage differences taking into consideration the other electrical parameters. 
       FIG. 5  shows a further exemplary embodiment of a combined ESR and capacitance measurement of a central energy reserve. 
     For this,  FIG. 1  is expanded by a further series transistor  119 . Series transistor  119  is connected by one outer electrode to battery voltage VZP and by the other outer electrode to coil  117 . The middle electrode is connected to a switch control  120 . Switch control  120  is controlled by microcontroller μC. Compared with  FIG. 1 , therefore, series transistor  119  has been inserted in the connection line between VZP and coil  117 . Otherwise, all components and connections are the same. 
     The passage of battery voltage to the energy reserve may be controlled by the μC using that transistor  119 . 
     If transistor  119  is switched off, it is also not possible for the energy reserve to be pre-charged by UB (VZP). 
     If transistor  119  is switched on, the ER is pre-charged to UB (VZP). 
     Thereafter, the energy reserve may be discharged slightly by the added current source without interference by UB at low ER voltage for capacitance measurement. The capacitance of ER may be calculated from Icap_test, the selected discharging time and the observed voltage level difference at ER. 
     Advantages of that exemplary embodiment are μC-controlled pre-charging of ER to UB (VZP). 
     An ER capacitance test at low ER voltage results in a reduction in the power loss in the measuring current source for capacitance measurement. 
     With the series transistor blocked, the ER capacitance measurement and ESR measurement may be carried out without interference by transients on the supply line, since the passage of UB (VZP) is prevented during the measurements. 
     The μC control lines μC-ON/OFF, μC-ON/OFF — 2, μC-ON/OFF — 3, apart from being directly connected to the μC, may also be controlled from a logic element present in the ASIC, that logic element communicating with the μC via a serial or parallel interface in order to receive the commands and acknowledge execution thereof.