Patent Publication Number: US-6904076-B1

Title: Interference canceller device and radio communication device

Description:
BACKGROUND OF THE INVENTION 
   The present invention relates to an interference canceller using an array antenna for a Direct Sequence Code Division Multiple Access (DS-CDMA) system and a radio communication device using such an interference canceller. 
   In the DS-CDMA system, a multi-rate transmission system including a plurality of transmission rates is known. Since the channel capacity is affected by interference between channels, it is necessary to provide an interference canceller for eliminating the interference between channels. A structure is known in which transmission power is reduced by using an array antenna to form a beam. The use of the array antenna results in a reduction in the interference due to spatial separation, which provides an improvement in the antenna gain. A RAKE receiver system capable of coping with multi-paths is also known. It is considered that the above-mentioned various techniques may arbitrarily be combined. In this case, it enables improved characteristics with an appropriate cost. 
   A transmitter part in a mobile radio communication system generally includes an encoder part performing error correction and encoding, a modulator part using a given modulation system such as QPSK, and a spread demodulator part. A receiver part which corresponds to the above transmitter part generally includes a spread demodulator part sing despreading, a modulator for demodulating a modulated wave of the QPSK or the like, and a decoder part performing error correction. 
     FIG. 10  is a diagram showing a conventional interference canceller. As can be seen, the interference canceller has a multi-stage parallel structure including a first stage, a second stage and a final stage. In this figure,  101  indicates an antenna,  102 - 1 ,  102 - 2  indicate delay circuits (DL),  103 - 11 - 103 - 1 k,  103 - 21 - 103 - 2 k indicate interference replicating units (IRU),  104 - 1 , 104 - 2  indicate adders, and  105 - 1 - 105 -k indicate receivers corresponding to different users. In the conventional interference canceller, it is possible to use only one stage or a number of stages. 
   In the first stage, a received signal is applied to the interference replicating units  103 - 11 - 103 - 1 k corresponding to the different user channels. The units  103 - 11 - 103 - 1 k then output symbol replicas SB and interference replicas d. The adder  104 - 1  subtracts the interference replicas d from the received signal obtained through the delay circuit  102 - 1 . 
   A resultant signal is applied to the second stage as an error signal e. 
   In the second stage, the interference replicating units  103 - 21 - 103 - 2 k units are provided with the error signal e from the first stage and the symbol replicas SB from the interference replica creating units  103 - 11 - 103 - 1 k. The interferencing cancelling units  103 - 21 - 103 - 2 k then output symbol replicas SB′ and interference replicas d. The adder  104 - 2  then subtracts the interference replica d′ from the error signal e supplied from the first stage via the delay circuit  102 - 2 . A resultant signal is applied, as an error signal e′ to the receivers  105 - 1 - 105 -k of the final stage. The receivers  105 - 1 - 105 -k which correspond to the different user channels perform a demodulation process by using the error signals e′ and the symbol replica SB′ from the second stage. Therefore, the received signal is obtained in each of the receivers  105 - 1 - 105 -k. 
     FIG. 11  is a diagram showing a conventional interference replicating unit. The reference number  103  indicates the interference replicating unit shown in FIG.  10 . In  FIG. 11 ,  111  indicates despread processing parts,  112  indicates respread processing parts,  113  indicates a despreading part,  114  indicates an adder,  115  indicates a channel estimation part,  116  indicates a multiplier,  117 ,  119  denote combining parts (Z),  118  indicates a decision part,  120  indicates a multiplier,  121  indicates an adder, and  122  indicates a respreading part. 
   The despread processing parts  111  and the respread processing parts  112  are provided in a parallel form taking into account that a signal is received through a plurality of propagation routes caused by reflection or the like. Hence, the parts  111 ,  112  are equal in number to the paths of the propagation routes. The despread processing parts  111  are each provided with a received signal, or the error signal e and the symbol replicas SB from the previous stage (the symbol replicas SB of the first stage are zero). In each of the despread processing parts  111 , the despreading part  113  despreads the received signal or the error signal e by a spreading code so that the demodulated signal can be obtained. The adder  114  then adds the symbol replica SB of the previous stage to the demodulated signal. The resultant output signal of the adder  114  is applied to the channel estimation part  115  and the multiplier  116 . The channel estimation part  115  applies a channel estimation value to the multipliers  116 ,  120 . 
   In this case, the received symbol is represented as Z·ξ where the known symbol such as a pilot signal is denoted as Z (complex number) and the propagation characteristic of the path is denoted as ξ (complex number). Thus, by multiplying the received symbol Z·ξ by the complex conjugate of the known symbol Z*, |Z| 2 ·ξ can be obtained. As described previously, since the symbol Z is known, the propagation characteristic of the path ξ is obtained. Therefore, the average value of the propagation characteristic t can be handled as a channel estimation value ξ{circumflex over ( 0 )}. 
   The complex conjugate (indicated by symbol *) of the channel estimation value ξ{circumflex over ( 0  )}. is input to the multiplier  116 , which multiplies the output signal of the adder  114  by the channel estimation value ξ{circumflex over ( 0 )}. The resultant output signals of the despread processing parts  111  are summed up by the combining part  117 , so that a path-diversity synthesized signal is obtained. In the path-diversity synthesized signal, the phase differences resulting from the propagation paths are already corrected. 
   The decision part  118  compares the synthesized output signal of the combining part  117  with a threshold value and the outputs provisionally decided data. In each of the respread processing parts  112 , the multiplier  120  multiplies the decision output signal of the decision part  118  by the channel estimation value output by the corresponding channel estimation part  115  is which is output to the next stage as a symbol replica SB of the corresponding path. The adder  121  calculates the difference between the symbol replica of the present stage and the symbol replica SB of the previous stage. The difference is respread by the spreading code by the respreading part  122 . The combining part  119  sums up the output signals of the respreading parts  122  corresponding to the respective paths and than outputs a resultant interference replica d, which is sent to the next stage. 
   The receivers  105 - 1 - 105 -k of the final stage shown in  FIG. 10  are configured by modifying the interference replicating unit  103  of  FIG. 11  so that the respread processing parts  112  are omitted and a demodulator is provided for modulating the resulting signal. The demodulated signal is sent to a network (not shown) in which a base station is connected. 
     FIGS. 12A and 12B  show an adaptive array receiver device. In particular,  FIG. 12A  shows a receiver device made up of array antenna elements  131 - 1 - 131 -m and adaptive array receivers  132 - 1 - 132 -k (AA receivers) corresponding to the different respective users.  FIG. 12B  shows the configuration for each of the adaptive array receivers  132 - 1   132 -k. In  FIG. 12B , reference number  133  indicates despread processing parts,  134 - 1 - 134 -m indicate despreading part,  135 - 1 - 135 -m indicate multipliers,  136  indicates a weight control part,  137 ,  138  indicate adders,  139  indicates a channel estimation part,  140 ,  141  indicate multipliers,  142  indicates a combining part (Σ), and  143  indicates a decision part. 
   The despreading parts  134 - 1 - 134 -m in each of the despread processing parts  133  are provided to the respective array antenna elements  131 - 1 - 131 -m. Each of the despreading parts  134  despread the received signal by using a spreading code supplied from a despreading code generator (not shown). The output signals of the despreading parts  134 - 1 - 134 -m are respectively applied to both the multipliers  135 - 1 - 135 -m and to the weight control part  136 . The weight control part  136  calculates weighting factors based on the output signals of the neighboring despreading parts  134 - 1 - 134 -m and the output signal of the adder  138 . 
   The weighting factors (complex numbers) have values depending on the directions in which the radio wave comes to the array antenna elements  131 - 1 - 131 -m. The multipliers  135 - 1 - 135 -m multiply the weighting factors by the despread output signals. The resultant output signals of the multipliers  135 - 1 - 135 -m are in phase with each other and are then applied to the adder  137 . The above adding process is known as a beam forming process. The channel estimation part  139  then produces a channel estimination value similar to the despread processing parts  111  of the interference replicating unit  103  of FIG.  11 . The multiplier  140  multiplies the output signal of the adder  137  (despread output signal) and the channel estimation value (complex conjugate). The resultant output signals of the despread processing parts  133  are then applied to the combining part  142 . 
   The combined output signal from combining part  142  is input to the decision part  143 , where it is compared with a threshold value for deciding data. The decision output signal from the decision part  142  is fed back to the multiplier to be multiplied by the channel estimation value so that a signal corresponding to the output signal of the adder  137  is obtained. The adder  138  calculates the difference between the output signal of the multiplier  141  and the output signal of the adder  137 . The difference thus calculated is input to the weight control part  136 , which produces the weighting factors having values that achieve optimal synthesizing in the adder  137 . 
     FIG. 13  shows a conventional RAKE receiver device, in which a reference number  151  indicates an antenna and  152  indicate finger parts. Reference number  153  indicates a searcher,  154  indicates a combining part,  155  indicates a decision part,  156  indicates a despreading part,  157  indicates a multiplier,  158  indicates a spreading code output part,  159  indicates a dump filter,  160  indicates a delay adjustment part (τ),  161  indicates a channel estimation part,  162  indicates a multiplier,  163  indicates matching filter,  164  indicates an averaging part,  165  indicates a memory (RAM) for storing a delay profile, and  166  indicates a path detection part which performs a finger allocation. 
   The RAKE receiver device allocates the finger parts  152  to the different paths in accordance with the delay profile obtained by the searcher  153 . The averaging part  164  of the searcher  153  averages the output signal from the matching filter  163 . The delay profile thus obtained is stored in the memory  165 . The path detection part  166  performs a path decision using the delay profile. For example, if a delay profile P shown in  FIG. 14  is obtained, the path detection part  166  compares the receive level with a threshold value TH 1  and detects paths P 1 , P 2  and P 3  that exceed the threshold value TH 1 . The path detection part  166  then allocates the paths P 1 , P 2  and P 3  to the first, second and third finger parts  152 , respectively. 
   The above allocation is attained by adjusting the delay times of the finger parts  152  in accordance with the phase differences among the paths P 1 , P 2  and P 3 . Then a start signals is applied to the spreading code output part  158  at the timings corresponding to the paths P 1 , P 2  and P 3 . Hence, the despreading process for the received signals is started. Therefore, the received signals obtained through the paths P 1 , P 2  and P 3  are synthesized so that the receive sensitivity is improved. 
   As has been described previously, the radio communication device of the DS-CDMA system is equipped with the interference canceller for eliminating interference from another channel, and thus improves the receive characteristics. Further, the radio communication device of the DS-CDMA system uses the array antenna and the adaptive array receiver that synthesizes the received signals on the basis of the directions in which the radio waves arrive at the array antenna elements. 
   However, a mere application of the array antenna to the DS-CDMA system to form the adaptive array receiver device makes the structure very complex and thus increases the cost of the system. Particularly, the complex structure also results from the unique arrangement of the DS-CDMA system in which radio communications are performed in a state in which high-rate channels of high transmission rates and low-rate channels of low transmission rates are mixed. 
   SUMMARY OF THE INVENTION 
   An object of the present invention is to simplify the structure of the interference canceller in order to reduce the cost of a radio communication device. 
   These and other objects are met according to the present invention by an interference canceller multi-rate transmission including at least low-rate channels and high-rate channels. The interference canceller includes an array antenna interference replicating unit for use in the high-rate channels. The array antenna replicating units receive signals corresponding to array antenna elements and creates interference replicas of the high-rate channels. An adder that subtracts the interference replicas generated by the array antenna interference replicating units from the received signals, and then outputs an interference-eliminated signal from which high-rate channel interference has been eliminated. Thus, interference of the high-rate channels having high transmission power is eliminated and the transmission quality of the low-rate channels is prevented from being degraded without requiring interference replicating unit for the low-rate channels. 
   The interference canceller according to the present invention also may be configured to include a searcher that detects paths based on a delay profile of the received signals and allocates finger parts to the paths that have been detected. The searcher includes a memory that stores a threshold value for detecting paths of the low-rate channels, a path detection unit that detect paths of the high-rate channels by using the threshold value stored in the memory and allocates the finger parts to the paths detected. 
   A radio communication device according to the present invention for a DS-CDMA communication system includes an interference canceller that receives signals via array antenna elements and receivers that receive interference-eliminated signals from the interference canceller and performs demodulation. The interference canceller includes array antenna interference replicating units for high-rate channels, and adders that subtract interference replicas from the array antenna interference replicating units from the signals received via the array antenna elements this enables resultant interference-eliminated signals to be applied to the receivers, wherein the receivers receiving the interference-eliminated signals perform demodulation. 
   The radio communication device according to the present invention is configured so that it further includes a searcher that detects paths based on a delay profile of one of the received signals obtained via at least one of the array antenna elements. The searcher allocates the finger parts to the paths detected. The searcher also includes a memory that stores a threshold value for detecting paths of the low-rate channels, a path detection unit that detects paths of the high-rate channels by using the threshold value stored in the memory and then allocates the finger parts to the paths detected. 
   The radio communication device according to the present invention also is configured so that the interference canceller includes an array antenna interference replicating units for the high-rate channels that receive the signals received via the array antenna elements. Adders also are included that subtract the interference replicas from the array antenna interference replicating units from the signals received via the array. Further, receivers have a structure that performs demodulation by beam forming using the interference-eliminated signals corresponding to the array antenna elements. 
   The radio communication device according to the present invention also is configured so that the interference canceller includes array antenna interference replicating units that create interference replicas of the high-rate channels and symbol replicas from the signals received via the array antenna elements. Further, adders are included to subtract the interference replicas from the array antenna interference replicating units from the signals received via the array antenna elements so that interference-eliminated signals are output. The receivers for the low-rate channels have a structure that performs demodulation by beam forming using the interference-eliminated signals corresponding to the array antenna elements. The receivers for the high-rate channels have a structure that performs demodulation by using the interference-eliminated signals corresponding to the array antenna elements and the symbol replicas. 
   The radio communication device according to the present invention also is configured so that the interference canceller includes an array antenna interference replicating unit for the high-rate channels that receive the signals received via the array antenna elements and interference replicas. Further, an adder subtracts the interference replicas from one of the signals received via the array antenna elements and applies a resultant interference-eliminated signal to the receivers for the low-rate channels. 
   The radio communication device according to the present invention also is configured so that the interference canceller includes array antenna interference replicating units for the high-rate channels that receive the signals received via the array antenna elements and creates interference replicas and symbol replicas. Further, an adder is included to subtract the interference replicas from the array antenna interference replicating units from one of the signals received via the array antenna elements. The receivers for the low-rate channels perform demodulation using the interference-eliminated signals. The receivers for the high-rate channels perform demodulation using the interference-eliminated signals and the symbol replicas. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
       FIG. 1  is a block diagram of a radio communication device according to the present invention; 
       FIG. 2  is a block diagram of an interference canceller according to the present invention; 
       FIG. 3  is a block diagram showing of an embodiment of an interference replicating unit according to the present invention; 
       FIG. 4  is a block diagram of another interference replicating unit with a searcher according to the present invention; 
       FIG. 5  is a graph illustrating a path detection for high-rate channels according to the present invention; 
       FIG. 6  is a block diagram of a radio communication device according to a first embodiment of the present invention; 
       FIG. 7  is a block diagram of a radio communication device according to a second embodiment of the present invention; 
       FIG. 8  is a block diagram of a radio communication device according to a third embodiment of the present invention; 
       FIG. 9  is a block diagram of a radio communication device according to a fourth embodiment of the present invention; 
       FIG. 10  is a block diagram of a conventional interference canceller, 
       FIG. 11  is a block diagram of a conventional interference replicating unit; 
       FIG. 12  is a block diagram of a conventional adaptive array device; 
       FIG. 13  is a block diagram of a conventional RAKE receiver device; and 
       FIG. 14  is a graph illustrating a conventional finger allocation process. 
   

   DETAILED DESCRIPTION 
     FIG. 1  shows a radio communication device according to an embodiment of the present invention. In this figure, reference numbers  1 - 1 - 1 -m indicate antenna array elements,  2  indicates a radio receiver part,  3  indicates an interference canceller,  4 - 1 - 4 -k indicate receivers corresponding to the different users,  5  indicates an array antenna interference replicating unit (AAIRU) for high-rate channels, and  6  indicates an adder that subtracts an interference replica from the received signals. The structure of  FIG. 1  corresponds to a receiver part of a base station in which communications are performed in the DS-CDMA system with low-rate channels and high-rate channels mixed. The receiver includes the components involved with the low-rate channels and the high-rate channels, and is connected to the network, an illustration of which is omitted. 
   The radio receiver part  2  includes, for each of the array antenna elements  1 - 1 - 1 -m, a low-noise amplifier, a band-pass filter, a frequency converter, a local oscillator, and an A/D converter. The radio receiver part  2  converts signals received via the array antenna elements  1 - 1 - 1 -m into digital signals, which are applied to the interference canceller  3 . The interference canceller  3  includes an array antenna interference replicating unit  5  for use in a high-rate channel, which eliminates an interference replica of the high-rate channel from the signal with the high-rate and low-rate channels mixed. 
   The transmission power for the high-rate channel is comparatively large which introduces large interference in the low-rate channels. In the present invention, the high-rate-channel-based interference in the received signals for the low-rate channel users is removed by removing the interference in the high-rate channels using the interference replicas created by the interference replicating unit  5 . This makes it possible to improve the receiving characteristics of the low-rate channels without providing an interference replicating unit for the low-rate channels. 
     FIG. 2  shows an interference canceller according to the present invention. In this figure,  1 - 1 - 1 -m indicate array antenna elements,  11 - 1 - 11 -m indicate delay circuits (DL),  12 - 1 - 12 -L indicate array antenna interference replicating units (AAIRU), and  13 - 1 - 13 -m indicate adders. An illustration of the radio receiver part is omitted for the sake of simplicity. 
   The signals received via the array antenna elements  1 - 1 - 1 -m are input to the array antenna interference replicating units  12 - 1 - 12 -L which create interference replicas of the high-rate channels. The adders  13 - 1 - 13 -m subtract the interference replicas of the high-rate channels from the received signals supplied via the delay circuits  11 - 1 - 1 -m. The resultant output signals of the adders  13 - 1 - 13 -m are applied to the user receivers (not shown) of the low-rate channels. Although, the structure shown in  FIG. 2  has a single stage, a multistage structure including a second stage can also be employed. A searcher  53  may also be included, which will be described in detail later. 
     FIG. 3  shows an embodiment of an interference replicating unit according to the present invention. In this figure, reference number  12  indicates the array antenna interference replicating unit for the high-rate channels. Reference number  14  indicates despread processing parts,  15  indicate respread processing parts,  16  and  18 - 1 - 18 -m indicate combining parts (Σ),  17  indicates a decision part,  21 - 1 - 21 -m indicate respreading parts,  22 - 1 - 22 -m indicate multipliers,  23  indicates an adder,  24  indicate multipliers,  26  indicates an adder,  27  indicates a channel estimation part,  28  indicates a weight control part,  29  indicates a multiplier,  30 - 1 - 30 -m indicate multipliers, and  31 - 1 - 31 -m indicate respreading parts. 
   The despread processing parts  14  all have the same structure in order to process multipaths. Similarly, the respread processing parts  15  have the same structures as each other also to process the multipaths. The despread processing parts  14  have the despreading parts  21 - 1 - 21 -m respectively corresponding to different array antenna elements. The despread output signals of the despreading parts  21 - 1 - 21 -m are respectively applied to the multipliers  22 - 1 - 22 -m and the weight control part  28 . The weight control part  28  is supplied with the difference between the output signal of the adder  23  and the output signal of the multiplier  25 . The above difference is output by the adder  26 . 
   The weight control part  28  calculates weight factors on the basis of the output signals of the neighboring despreading parts  21 - 1 - 21 -m and the difference output by the adder  26 . The weight factors calculated are than input to the multipliers  22 - 1 - 22 -m,  30 - 1 - 30 -m The despread output signals are multiplied by the weight factors by the multipliers  22 - 1 - 22 -m. The despread output signals which are brought in phase in the above manner are added by the adder  23 . The output signal of the adder  23  is applied to the multiplier  23 , channel estimation part  27  and the adder  26 . 
   As has been described previously, the channel estimation part  27  obtains a channel estimation part using a known symbol. The complex conjugate (denoted by *) of the estimation value is input to the multiplier  24 , which receives the output signal of the adder  23 . Thus, the output signals of the despread processing parts  14  are brought in phase and are applied to the combining part  16 . The decision part  17  provisionally makes a decision on the output signal of the combining part  16 . The output signal of the decision part  17  is applied to the multiplier  25  of the despread processing parts  14  and the multiplier  29  of the respread processing parts  15 . Only the known symbol used when the channel estimation value is calculated may be used as the input to the multipliers  25 . 
   In each of the respread processing parts  15 , the multiplier  29  multiplies the provisionally decided data by the channel estimation value so that the original state is obtained. The multipliers  30 - 1 - 30 -m multiply the output signal of the multiplier  29  by the complex conjugate (*) of the weight factors so that the states of the spread output signals of the despreading parts  21 - 1 - 21 -m are obtained. The respreading parts  31 - 1 - 31 -m perform the respreading operations on the output signals of the multipliers  30 - 1 - 30 -m. The combining parts  18 - 1 - 18 -m then combine the respread output signals corresponding to the different paths, so that interference replicas are produced. The output signals of the multipliers  29  are used as symbol replicas after the array antenna combining. Further, the output signals of the multipliers  30 - 1 - 30 -m are handled as replicas of the antenna elements. 
   The structure obtained by omitting the aforementioned respread processing parts is equivalent to the adaptive array receiver device shown in FIG.  12 . In the present invention, the array antenna interference replicating unit  12  for the high-rate channels is configured to include the respread processing parts  15 . Hence, it is possible to eliminate the high-rate-channel-based interference in the low-rate channels and ensure the transmission qualities of the low-rate channels with a less-expensive structure 
     FIG. 4  shows another interference replicating unit with a searcher according to the present invention. Reference numbers  1 - 1 - 1 -m indicate antenna elements,  14  indicate despread processing parts,  53  indicates a searcher,  16  indicates a combining part,  17  indicates a decision part,  56  indicates a matched filter,  57  indicates an averaging part,  58  indicates a memory (RAM) storing a delay profile,  59  indicates a path detection part,  60  indicates a memory (RAM) storing a threshold value for path detection for low-rate channels,  21 - 1  to  21 -m indicate despreading parts,  31 - 1  to  31 -m indicate respreading parts,  62 - 1  to  62 -m indicate multipliers,  63 - 1 ,  63 - 2  indicate spreading code generators,  64 - 1  to  64 -m indicate dump filters,  65 - 1  to  65 -m indicates delay adjustment parts (X),  27  indicates a channel estimator, and  24  indicates a multiplier. The antenna elements  1 — 1  to  1 -m receive signals which are input to the searcher  53 . 
   The searcher  53  is made up of the matched filter  56 , the averaging part  57 , the memory  58  for storing the delay profile, the path detection part  59  and the memory  60  for storing the threshold value for the paths of the low-rate-channels. The searcher  53  is used to allocate the despread processing parts  14  and the respread processing parts  15  to the paths. 
     FIGS. 5A and 5B  shows the path detection for the high-rate channels. In particular,  FIG. 5A  shows a delay profile for low-rate channels, while  FIG. 5B  shows a delay profile for high-rate channels. In the delay profile of the low-rate channels shown in FIG. SA, as in the case previously described with reference to  FIG. 14 , the path detection part  59  sets for the low-rate channels, a threshold value TH 1  based on the delay profile stored n the memory  58  and the averaged received signal output by the averaging part  57 . The path detection part  59  then allocates paths P 1 , n and P 3  having levels exceeding the threshold value TH 1  to the finger parts. In the delay profile for the high-rate channels shown in FIG.  5 (B), the prior art path detection part  59  sets a threshold value TH 2  on the basis of the above delay profile, and allocates the paths P 1 , P 2  and P 3  having levels exceeding the threshold value TH 2  to the finger parts. 
   However, in the high-rate channels, there is a possibility that received levels may not exceed the threshold value TH 2 , but may exceed the threshold value TH 1  for the low-rate channels. If the number of paths is larger than the number of despread processing parts  14 , the interference may not effectively be eliminated. In view of the above problem, according to the present invention the threshold value TH 1  for detecting paths of the low-rate channels is stored in the memory  60 . The stored threshold value TH 1  is read therefrom at the time of detecting paths of the high-rate channels by the path detection part  53 . The threshold value TH 1  read from the memory  60  is then used as the threshold value for detecting paths of the high-rate channels. 
   Hence, at the time of detecting paths of the high-rate channels, the path detection part  59  detects paths having levels exceeding the threshold value TH 1  for detecting paths of the low-rate channels. Thus, in the case shown in FIG.  5 (B), paths P 1 -P 5  are detected. The parts  14  are allocated to the detected paths P 1 -P 5 . As described above, an increased number of despread processing parts  14  is employed in order to detect an increased number of paths at the time of detecting paths of the high-rate channels. 
   Hence, it is possible to effectively control interference in the high-rate channels in which high transmission power is used. Referring back to  FIG. 4 , the searcher  53  is applied to the path-based allocation in the despreading processing parts  14  in the interference replicating unit  12 . Thus, it is possible to produce the interference replicas of the high-rate channels. That is, instead of omitting the interference replicating unit for the low-rate channels, the interference replicas for the highly-precise, high-rate channels can be produced from the interference replicating unit for the high-rate channels. 
     FIG. 6  shows a radio communication according to a first embodiment of the present invention. The structure shown in  FIG. 6  corresponds to a receiver part of the base station in the DS-CDMA system, wherein the structure shown in  FIG. 2  is applied to the receiver part. In  FIG. 6 , reference numbers  1 - 1 - 1 -m indicate array antenna elements,  11 - 1 - 11 -m indicate delay circuits (DL),  12 - 1 - 12 -L array antenna interference replicating units (AAIRU) for the high-rate channels,  13 - 1 - 13 -m indicate adders,  60 - 1 - 60 -k indicate adaptive array receivers (AA receivers) for low-rate users, and  61  indicates an interference canceller. 
   The array antenna interference replicating units  12 - 1 - 12 -L have the structure shown in  FIG. 3 , and create interference replicas of the high-rate channels. The adders  13 - 1 - 13 -m subtract the interference replicas d from the received signals obtained via the delay circuits  11 - 1 - 11 -m. As have been described previously, the delay circuits  11 - 1 - 11 -m compensate for delays in time caused by the processes of the array antenna interference replicating units  12 - 1 - 12 -L. 
   The adaptive array receivers  60 - 1 - 60 -k may have a structure, for example, as shown in FIG.  12 . That is, demodulation can be performed based on the received signal obtained by the combining after the beam forming. Although the receivers for the high-rate users are not shown for the sake of simplicity, it is possible to use the decision outputs of the decision parts  17  (see  FIG. 3 ) in the array antenna interference replicating units  12 - 1 - 12 -L. The symbol replica cannot be used because the channel estimation value is multiplied and the symbol replica is obtained before being phase corrected. Although,  FIG. 6  shows only one stage, a multistage structure may be used. 
     FIG. 7  shows a radio communication device according to a second embodiment of the present invention. The structure shown in  FIG. 7  is simpler than that shown in FIG.  6 . In  FIG. 7 , reference numbers  71 - 1 - 71 -m indicate array antenna elements,  72  indicates an interference canceller,  73  indicates a delay circuit (DL),  74 - 1 - 74 -L indicate array antenna interference replicating units ((AAIRU),  75  indicates an adder, and  76 - 1 - 76 -k indicate receivers of low-rate users. 
   The signals received via the array antenna elements  71 - 1 - 71 -m are input to the array antenna interference replicating units  74 - 1 - 74 -L. The signal received via the array antenna element  71 - 1  is input to the receivers  76 - 1 - 76 -k, via the delay circuit  73  and the adder  75 . The adder  75  subtracts the interference replicating d from the array antenna interference replicating units  74 - 1 - 74 -L from the signal obtained via the delay circuit  73 , so that interference of the high-rate channels having high transmission power are eliminated. The interference-eliminated signal is then input to the low-rate user receivers  76 - 1 - 76 -k, which perform the demodulation process. Even in this case, it is possible to use the decision outputs of the decision parts in the array antenna interference replicating units  74 - 1 - 74 -L. 
     FIG. 8  shows a radio communication device according to a third embodiment of the present invention. In this figure, reference numbers  81 - 1 - 81 -m indicate array antenna elements,  82  indicates an interference canceller,  83 - 1 - 83 -m indicate delay circuits (DL),  84 - 1 - 84 -L indicate array antenna interference replicating units (AAIRU),  85 - 1 - 85 -m indicate adders,  86 - 1 - 86 -k indicate adaptive array receivers (AA receivers) for low rate users, and  87 - 1 - 87 -L indicate adaptive array receivers (AA receivers) for high-rate users. 
   The array antenna interference replicating units  84 - 1 - 84 -L have a structure similar to that of the array antenna interference replicating units in the aforementioned embodiments of the present invention. Signals received via the array antenna elements  81 - 1 - 81 -m are applied to the array antenna interference replicating units  84 - 1 - 84 -L. Hence, interference replicas of the high-rate channels and symbol replicas are created. The interference replicas thus created are respectively applied to the adders  85 - 1 - 85 -m, which subtract the received replicas from the received signals obtained via the array antenna elements  81 - 1 - 82 -m. Interference-eliminated signals which do not have interference of the high-rate channels are then input to the adaptive array receivers  86 - 1 - 86 -k of the low-rate users and the adaptive array receivers  87 - 1 - 87 -L of the high-rate users. These receivers may have a structure as shown in  FIG. 12 , for example. 
   The adaptive array receivers  86 - 1 - 86 -k for the low-rate users perform the demodulation process on the basis of the combined signal obtained by the beam forming using the interference-eliminated signals. The adaptive array receivers  87 - 1 - 87 -L for the high-rate users perform the demodulation process on the basis of the interference-eliminated signals from the adders  85 - 1 - 85 -m and the symbol replicas from the array antenna interference replicating units  84 - 1 - 84 -L. The adaptive array receivers  87 - 1 - 87 -L for the hi rate users have a structure that is, for example, a combination of the despread processing parts  14  shown in  FIG. 3 , the despread processing parts  11 I shown in FIG.  11  and the despread processing parts  133  shown in FIG.  12 . 
     FIG. 9  shows a radio communication device according to a fourth embodiment of the present invention. In this figure, reference numbers  91 - 1 - 91 -m indicate array antenna elements,  92  indicates an interference canceller,  93  indicates a delay circuit (DL),  94 - 1 - 94 -L indicate array antenna interference replicating units (AAIRU),  95  indicates an adder,  96 - 1 - 96 -k indicate receivers for the low-rate users, and  97 - 1 - 97 -L indicate receivers for the high-rate users. The array antenna interference replicating units  94 - 1 - 94 -L have the same structure as that of the array antenna interference creating units in the aforementioned embodiments of the present invention. 
   As in the case of the structure shown in  FIG. 7 , a signal received via one of the array antenna elements  91 - 1 - 91 -m, namely, array antenna elements  91 - 1  in  FIG. 8  is delayed by the delay circuit  83 - 1  and is then applied to the adder  85 - 1 . Interference replicas and symbol replicas are created by the array antenna interference replicating units  94 - 1 - 94 -L, which receive the signals received via the array antenna elements  91 - 1 - 91 -m. The interference replicas are applied to the adder  95 , which subtracts the received interference replicas from the received signal applied via the delay circuit  93 . Hence, an interference-eliminated signal is obtained. 
   The interference-eliminated signal obtained is applied to the receivers  96 - 1 - 96 -k for the low-rate users and the receivers  97 - 1 - 97 -L for the high-rate users. The low-rate user receiving  96 - 1 - 96 -k perform the demodulation process using the symbol replicas from the array antenna interference replicating units  94 - 1 - 94 L and the interference-eliminated signal from the adder  95 . 
   The present invention is not limited to the aforementioned embodiments, but various variations and modifications may be made. For example, the searcher shown in  FIG. 4  in which the path detection for the high-rate channels can be performed using the threshold value TH 1  for the path detection for the low-rate channels may be applied to other embodiments of the present invention. 
   As described above, the present invention is directed to an interference canceller for the DS-CDMA communication system, which performs multi-rate transmission including low-rate channels and high-rate channels, and a radio communication device using the same. Radio waves are received through the array antennas, and the array antenna interference replicating unit is provided, which creates interference replicas for the high-rate channels. Thereby, the interference of the high-rate channels to the received signals can be eliminated. 
   Further, without the interference replicating unit for the low-rate channels, the interference of the high-rate channels is eliminated and the transmission qualities of the low-rate channels are improved. Thus, the present invention is less expensive than the case where the array antenna interference replicating units are respectively provided to all the channels of the multi-rate transmission. Although, the structure of the invention is simple, the invention eliminates interference of the high-rate channels having high power.