Patent Publication Number: US-8126092-B2

Title: Multistage PN code acquisition circuit and method

Description:
CLAIM TO PRIORITY OF PROVISIONAL APPLICATION 
     This application claims priority under 35 U.S.C. 120 of divisional application Ser. No. 09/533,311, filed Mar. 22, 2000, now U.S. Pat. No. 6,831,929, which claims priority under 35 U.S.C. §119(e)(1) of provisional application Ser. No. 60/125,443, filed Mar. 22, 1999. 
    
    
     FIELD OF THE INVENTION 
     This invention relates to wideband code division multiple access (WCDMA) for a communication system and more particularly to detection of primary or secondary synchronization codes for WCDMA cell acquisition. 
     BACKGROUND OF THE INVENTION 
     Present code division multiple access (CDMA) systems are characterized by simultaneous transmission of different data signals over a common channel by assigning each signal a unique code. This unique code is matched with a code of a selected receiver to determine the proper recipient of a data signal. These different data signals arrive at the receiver via multiple paths due to ground clutter and unpredictable signal reflection. Additive effects of these multiple data signals at the receiver may result in significant fading or variation in received signal strength. In general, this fading due to multiple data paths may be diminished by spreading the transmitted energy over a wide bandwidth. This wide bandwidth results in greatly reduced fading compared to narrow band transmission modes such as frequency division multiple access (FDMA) or time division multiple access (TDMA). 
     New standards are continually emerging for next generation wideband code division multiple access (WCDMA) communication systems as described in U.S. patent application Ser. No. 90/217,759, entitled Simplified Cell Search Scheme for First and Second Stage, filed Dec. 21, 1998, and incorporated herein by reference. These WCDMA systems are coherent communications systems with pilot symbol assisted channel estimation schemes. These pilot symbols are transmitted as quadrature phase shift keyed (QPSK) known data in predetermined time frames to any receivers within the cell or within range. The frames may propagate in a discontinuous transmission (DTX) mode within the cell. For voice traffic, transmission of user data occurs when the user speaks, but no data symbol transmission occurs when the user is silent. Similarly for packet data, the user data may be transmitted only when packets are ready to be sent. The frames include pilot symbols as well as other control symbols such as transmit power control (TPC) symbols and rate information (RI) symbols. These control symbols include multiple bits otherwise known as chips to distinguish them from data bits. The chip transmission time (T C ), therefore, is equal to the symbol time rate (T) divided by the number of chips in the symbol (N). This number of chips in the symbol is the spreading factor. 
     Previous WCDMA base stations have broadcast primary (PSC) and secondary (SSC) synchronization codes to properly establish communications with a mobile receiver. The PSC identifies the source as a base station within the cell. The SSC further identifies a group of synchronization codes that are selectively assigned to base stations that may transmit within the cell. Referring now to  FIG. 1 , there is a simplified block diagram of a circuit of the prior art for generating primary and secondary search codes. These search codes modulate or spread the transmitted signal so that a mobile receiver may identify it. Circuits  102  and  110  each produce a 256 cycle Hadamard sequence at leads  103  and  111 , respectively. Either a true or a complement of a 16-cycle pseudorandom noise (PN) sequence, however, selectively modulates both sequences. This 16-cycle PN sequence is preferably a binary Lindner sequence given by Z={1,1,−1,−1,−1,−1,1,−1,1,1,−1,1,1,1,−1,1}. Each element of the Lindner sequence is further designated z 1 -z 16 , respectively. Circuit  108  generates a 256-cycle code at lead  109  as a product of the Lindner sequence and each element of the sequence. The resulting PN sequence at lead  109 , therefore, has the form {Z,Z,−Z, −Z,−Z,−Z,Z,−Z,Z,Z,−Z,Z,Z,Z,−Z,Z}. Exclusive-OR circuit  112  modulates the Hadamard sequence on lead  111  with the PN sequence on lead  109 , thereby producing a PSC on lead  114 . Likewise, exclusive-OR circuit  104  modulates the Hadamard sequence on lead  103  with the PN sequence on lead  109 , thereby producing an SSC on lead  106 . 
     A WCDMA mobile communication system must initially acquire a signal from a remote base station to establish communications within a cell. This initial acquisition, however, is complicated by the presence of multiple unrelated signals from the base station that are intended for other mobile systems within the cell as well as signals from other base stations. The base station continually transmits a special signal at 16 KSPS on a perch channel, much like a beacon, to facilitate this initial acquisition. The perch channel format includes a frame with sixteen time slots, each having a duration of 0.625 milliseconds. Each time slot includes four common pilot symbols, four transport channel data symbols and two search code symbols. These search code symbols include the PSC and SSC symbols transmitted in parallel. These search code symbols are not modulated by the long code, so a mobile receiver need not decode these signals with a Viterbi decoder to properly identify the base station. Proper identification of the PSC and SSC by the mobile receiver, therefore, limits the final search to one of sixteen groups of thirty-two comma free codes each that specifically identify a base station within the cell to a mobile unit. 
     Referring to  FIG. 2 , there is a circuit of the prior art for detecting the PSC and SSC generated by the circuit of  FIG. 1 . The circuit receives the PSC symbol from the transmitter as an input signal IN on lead  200 . The signal is periodically sampled in response to a clock signal by serial register  221  at an oversampling rate n. Serial register  221 , therefore, has 15*n stages for storing each successive sample of the input signal IN. Serial register  221  has 16 (N) taps  242 - 246  that produce 16 respective parallel tap signals. A logic circuit including 16 XOR circuits ( 230 ,  232 ,  234 ) receives the respective tap signals as well as sixteen respective PN signals to produce sixteen output signals ( 231 ,  233 ,  235 ). This PN sequence matches the transmitted sequence from circuit  108  and is preferably a Lindner sequence. Adder circuit  248  receives the sixteen output signals and adds them to produce a sequence of output signals at terminal  250  corresponding to the oversampling rate n. An oversampling rate of n=1, for example, corresponds to one sample per chip, 256 samples per symbol, 2560 samples per time slot, and 40,960 samples per frame. 
     A 16-symbol accumulator circuit  290  receives the sequence of output signals on lead  250 . The accumulator circuit  290  periodically samples the sequence on lead  250  in serial register  291  in response to the clock signal at the oversampling rate n. Serial register  291 , therefore, has 240*n stages for storing each successive sample. Serial register  291  has sixteen taps  250 - 284  that produce sixteen respective parallel tap signals. Inverters  285  invert tap signals corresponding to negative elements of the Lindner sequence. Adder circuit  286  receives the sixteen output signals and adds them to produce a match signal MAT at output terminal  288  in response to an appropriate PSC symbol. This match result is subsequently stored in a buffer memory. In this manner, the match filter circuit samples the entire PN sequence at lead  200  for one frame of 10 milliseconds. Thus, the match filter detects a PSC symbol common to each time slot and an SSC symbol corresponding to each respective time slot. After the 10-millisecond sample period of first-stage cell acquisition, the match filter is reset and repeats the match process for a next frame. The previously acquired time of the PSC symbol match as well as the sixteen SSC symbols are passed to a second-stage of cell acquisition. 
     Referring to  FIG. 3 , there is a diagram showing cell acquisition of the prior art. The first-stage cell acquisition begins at time  301  when the first-stage  300 , including match filter  220 ,  290  and buffer memory (not shown) are reset. The first-stage circuit  300  sequentially samples a PN sequence at lead  200  for 10 milliseconds. The results of the PSC symbol match from the first-stage circuit are passed  306  to a second-stage circuit  312  and the first-stage circuit is reset  303 . The first-stage circuit  302  repeats the match sequence for the next 10-millisecond period. The second-stage circuit receives the sample time of the PSC symbol and determines the time of each SSC symbol in each time slot by a cumulative 0.625 millisecond offset of each sequential SSC symbol. The second-stage circuit decodes this sequence of SSC symbols to identify the position within the frame of the first PSC symbol match as well as which one of sixteen code groups are received from the base station. The code group identity is then passed  318  to a third-stage circuit  324 . The third-stage circuit identifies one of thirty-two long code sequences in the code group that will be used to demodulate received data symbols. 
     These circuits of the prior art require significant memory and processing power to generate and identify the PSC and SSC. For example, each delay circuit  222 ,  224 ,  252  and  254  requires a memory cell for each PN sample. The subsequent buffer memory requires a similar memory size to store samples for second-stage cell acquisition. Moreover, a higher sample rate n requires a correspondingly greater memory size. An alternative scheme of Code Position Modulation (CPM) has been proposed which does not require a PSC match. This CPM scheme places SSC symbols at various symbol times within a PN sequence frame. The match filter must then correctly match the SSC symbol in each time slot of the frame and use the position of the SSC symbols within their respective time slots to determine the correct code group for second-stage cell acquisition. This method advantageously eliminates the step of PSC matching. The requirement to independently match and identify the position of each SSC symbol of the frame, however, results in increased circuit complexity without tangible gain. 
     Other studies such as by Ericsson,  Comparisons of Cell Search Schemes.  3 GPP Versus CPM , Feb. 26, 1999, have suggested that CPM acquisition is inferior to the existing 3GPP acquisition procedure as described with respect to  FIG. 2 . Furthermore, their study suggests that first-stage acquisition may be improved by continually accumulating the match filter output of the PSC symbol without resetting the match filter or subsequent buffer memory. This technique, however, presents other problems in first-stage cell acquisition. During initial acquisition by a mobile receiver after power-up, the mobile uses an internal clock to time PN sequence samples. This internal clock frequency is typically much less stable than the base station clock frequency. Moreover, it is not synchronized with the base station clock frequency and may experience a relative clock frequency drift of several KHz. This clock frequency drift during initial acquisition, therefore, increasingly disperses the initial PSC symbol match with each accumulated frame sample. This dispersion with increasing frame samples reduces the probability P 1  of a correct first-stage PSC symbol match. 
     SUMMARY OF THE INVENTION 
     These problems are resolved by a circuit for detecting a serial signal comprising a first circuit coupled to receive the serial signal during a predetermined plurality of time periods of substantially equal duration. The first circuit is coupled to receive a first code and compares a part of the serial signal corresponding to each time period of the plurality of time periods to the first code, thereby producing a match signal. The first circuit accumulates the match signal from each time period of the plurality of time periods. 
     The present invention improves cell acquisition. Clock frequency drift is minimized during initial acquisition. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       A more complete understanding of the invention may be gained by reading the subsequent detailed description with reference to the drawings wherein: 
         FIG. 1  is a simplified block diagram of a typical transmitter circuit of the prior art for producing primary (PSC) and secondary (SSC) synchronization codes; 
         FIG. 2  is a block diagram of a mobile receiver match filter circuit of the prior art for first-stage cell acquisition; 
         FIG. 3  is a cell acquisition diagram of the prior art; 
         FIG. 4  is a block diagram of an embodiment of a cell acquisition circuit of the present invention; 
         FIG. 5  is a block diagram of a first-stage circuit that may be used by the cell acquisition circuit of  FIG. 4 ; 
         FIG. 6  is a block diagram of a second-stage circuit that may be used by the cell acquisition circuit of  FIG. 4 ; 
         FIG. 7  is a cell acquisition diagram for the circuit of  FIG. 4  of the present invention; 
         FIG. 8  is a cell acquisition diagram for another embodiment of the circuit of  FIG. 4  of the present invention; 
         FIG. 9  is a simulation showing initial cell acquisition time as a function of the probability of acquisition; and 
         FIG. 10  is a simulation showing handoff cell acquisition time as a function of the probability of acquisition. 
     
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     A mobile unit must select a base station from several candidate base stations at power-up and during soft handoff within a cell. The selection process is based on received power from each base station. There may, however, be as many as twenty candidate base stations to evaluate during the selection process. Selection of a particular base station requires cell acquisition of each base station to develop a candidate list. This cell acquisition includes three stages as previously described. The first stage includes detecting a primary synchronization channel (PSC) code from a serial pseudorandom noise (PN) sequence. This PSC code is common to all base stations within a network and to each time slot of a received frame. First-stage acquisition, therefore, may identify any of several PSC codes. Second-stage acquisition uses the time of the PSC code to extract a code from a secondary synchronization channel (SSC). This SSC code includes sixteen code sequences and is transmitted simultaneously with the PSC code. The SSC code, however, is unique to each base station. Furthermore, the order of the SSC code sequences identifies the position within the frame where the PSC code was identified during first-stage acquisition and a group of thirty-two long codes used by the base station. Finally, in third-stage acquisition, the mobile unit must identify the one of thirty-two long code sequences to demodulate the received signal. 
     The time required for cell acquisition Tacq is approximately equal to Tacc/Pd, where Tacc is the time required by the first stage and Pd is the probability of detection. The probability of detection Pd may typically have a value of 0.1, and Tacc typically has a value of 10 milliseconds. During initial acquisition at power-up, however, the mobile receiver internal clock is not synchronized with the base station clock and the Pd may be significantly less than 0.1. Thus, the first stage may dominate the three-stage acquisition process during power-up. 
     Referring now to  FIG. 4 , there is a block diagram of an embodiment of a cell acquisition circuit of the present invention. The circuit includes a first-stage circuit  400  that is coupled to receive a serial PN sequence on lead  200 . The serial PN sequence signal includes a data frame having a predetermined plurality of preferably sixteen time slots. Each time slot has a duration of approximately 0.625 milliseconds. The serial PN sequence is sampled by the first-stage circuit at a rate determined by clock signal CLK at lead  412 . The sample is preferably an integral multiple n of the chip time. The first-stage circuit  400  is also coupled to receive a PSC code on lead  414 . The first-stage circuit compares each sample of the serial PN sequence signal to the PSC code and produces a match signal at lead  402 . A frequency divider circuit  418  is coupled to receive the clock signal CLK at lead  412  and a power-up signal at lead  413 . The frequency divider circuit divides the clock signal CLK frequency by N to produce a reset signal RST on lead  416 . This reset signal RST is applied to the first-stage circuit  400  to reset accumulated decision variables. When the power-up signal is high at initial power-up, the frequency divider divides by N preferably having a value of 32*2560 corresponding to thirty-two time slots. The first-stage circuit, therefore, accumulates the result of the PSC code comparison to the serial PN sequence during power-up over thirty-two time slots to produce the match signal at lead  402 . Alternatively, when the power-up signal is low during a soft handoff from one base station to another, the frequency divider divides by N preferably having a value of 16*2560 corresponding to sixteen time slots. The first-stage circuit, therefore, accumulates the result of the PSC code comparison to the serial PN sequence during soft handoff over sixteen time slots to produce the match signal at lead  402 . 
     This variable accumulation offers significant advantages in first-stage acquisition. First, the mobile unit improves first-stage acquisition significantly during power-up by accumulating the PN sequence and PSC code match result over a predetermined number of time slots. The first-stage circuit is reset after this predetermined number of accumulations, thereby minimizing secondary match signals due to clock frequency drift. Second, overall cell acquisition time is minimized during soft handoff periods when the mobile clock frequency is synchronized to a stable base station clock frequency. Third, the present invention is completely compatible with existing communication standards. Finally, minimal additional circuitry is required to implement the present invention. 
     The PSC match signal at lead  402  is applied to the second-stage circuit  404 . The match signal includes an accumulated maximum value at a chip time corresponding to a match between the serial PN sequence and the PSC code. The second-stage circuit also receives the PN sequence on lead  200  and the SSC codes on lead  415 . The second-stage circuit extracts sixteen SSC symbols corresponding to the PSC match time for each of the sixteen time slots. The second-stage circuit compares these sixteen extracted SSC symbols to the SSC codes on lead  415  to determine their order as well as their position within the received frame. The second-stage circuit decodes these SSC symbols to identify the frame timing and code group corresponding to the received signal as will be described in detail. This code group identity is passed to a third-stage circuit  408  via lead  406 . The third-stage circuit determines which of thirty-two long codes in the identified code group has been received. The third-stage circuit produces this long code identity match signal on lead  410 . The long code identity match signal is used by the mobile receiver to demodulate the received signal from the remote base station. 
     Referring now to  FIG. 5 , there is a block diagram of a first-stage circuit that may be used by the cell acquisition circuit of  FIG. 4 . The first-stage circuit includes a match filter circuit  500  that is coupled to receive the serial PN sequence on lead  200  and the PSC code on lead  414 . The match filter circuit  500  produces a match signal at lead  502  having a level corresponding to each sample time of the clock signal CLK at lead  412 . This match signal at lead  502  is added to the recirculated contents of buffer memory circuit  508  on lead  402  by adder circuit  504 . A sum signal from adder circuit  504  is returned to buffer memory circuit  508  via lead  506 . Thus, the output signal from match filter circuit  500  accumulates in buffer memory circuit  508  as long as reset signal RST at lead  416  is low and produces a PSC match signal at lead  402 . When reset signal RST at lead  416  goes high, the contents of buffer memory circuit  508  is reset to an all-zero state in preparation for the next match signal accumulation. 
     Turning to  FIG. 6 , there is a block diagram of a second-stage circuit that may be used by the cell acquisition circuit of  FIG. 4 . This second-stage circuit includes a match filter circuit  600 , a slot buffer memory circuit  603  and a group decoder circuit  604 . The match filter circuit is coupled to receive the PN sequence on lead  200  and the PSC match signal on lead  402 . The match filter also receives sixteen SSC codes on bus  415 . Results of the match filter compare are applied to the slot buffer memory circuit  603  via bus  601 . The slot buffer memory circuit  603  has sixteen memory locations for each of sixteen respective sampled time slots. The sixteen SSC code symbol compare values are applied to group decode circuit  604  via bus  602 . Group decode circuit  602  decodes the SSC symbols to identify one of sixteen possible code groups and to determine which of sixteen time slots produced the PSC code match. Group decode circuit  604  produces decoded output signals on bus  406  corresponding to the sequence of SSC code symbols. These decoded output signals are applied to the third-stage decode circuit  408  to complete cell acquisition. 
     In operation, the match filter circuit  600  compares the PN sequence to each of the sixteen SSC codes on bus  415  at the times indicated by the PSC match signal. The match filter circuit produces sixteen match signals on bus  601  corresponding to each time slot. One of the sixteen match signals has a magnitude substantially greater than the other fifteen indicating an SSC code match. The other fifteen signals are comprise noise. All sixteen match signals for each of sixteen time slots are stored in slot buffer memory circuit  603 . The group decode circuit  604  adds the maximum value match signal from each respective time slot to produce a decision variable. The group decode circuit also adds each cyclic shift of the maximum value match signal to produce fifteen other decision variables. These fifteen other decision variables are preferably additive noise. A comparison of the maximum decision variable with fifteen other decision variables produces the order of SSC codes as well as their position within the frame. This soft decision process is highly advantageous in decoding the SSC codes. Correct SSC code symbol match values from each time slot reinforce each other and increase the value of the resulting decision variable. Incorrect SSC code symbol match values add as noise. Thus, a comparison or soft decision from decision variables produces an improved signal-to-noise ratio compared to a hard decision based on the magnitude of each individual SSC code symbol value. 
     Referring now to  FIG. 7 , there is a cell acquisition diagram for the circuit of  FIG. 4  of the present invention. During a soft handoff acquisition, cell acquisition begins with a reset signal at time  704  to clear buffer memory circuit  508 . The buffer memory circuit then accumulates a match signal over 20 milliseconds during stage  1 A ( 700 ) and stage  1 B ( 702 ). This accumulation period may include a part of a first frame, a complete second frame, and a part of a third frame. This sample period assures acquisition of two PSC symbols and two SSC symbols for each time slot of at least two frames. The accumulated result is passed to stage  2  ( 710 ) at time  708 . The first stage circuit is then reset at time  706  and begins to accumulate a match signal for another 20 milliseconds during stage  1 A ( 716 ) and stage  1 B ( 718 ). The second-stage circuit  404  decodes the result of the first-stage match and passes the result to stage  3  ( 714 ) at time  712 . Thus, the first-stage acquisition of the present invention advantageously provides for match signal accumulation over a predetermined number of frames. This first-stage accumulation period ( 716 ,  718 ) proceeds in parallel with second-stage  710  and third-stage  714  acquisition periods, thereby minimizing overall cell acquisition time. 
     Referring to  FIG. 8 , there is an alternative embodiment of a cell acquisition diagram for the circuit of  FIG. 4  of the present invention. Cell acquisition may optimally require a greater predetermined number of accumulated samples. The first stage accumulation process, therefore, is partitioned into overlapping banks to minimize cell acquisition time. The first-stage accumulation begins with bank  2 . Stages  1 C ( 814 ) and  1 D ( 816 ) terminate the bank  2  accumulation and pass the result to stage  2  ( 820 ) at time  818 . Stage  2  decoding  820  is completed at time  822  and passes the result to stage  3  ( 824 ) at time  822 . Meanwhile, the next first-stage accumulation of bank  2  begins with stage  1 A ( 830 ) and extends through stage  1 D ( 836 ). First-stage accumulation by bank  1  begins with the reset signal at time  800  and proceeds for 40 milliseconds until the reset signal at time  802 . The bank  1  accumulation includes stages  1 A- 1 D ( 804 - 810 ) and overlaps with bank  2  accumulation. Upon completion of bank  2  accumulation, the result passes to stage  2  ( 842 ) at time  826 . Bank  1  is then reset  802  and begins the next period of accumulation. The overlapping banks advantageously provide for extended first-stage accumulation without increasing overall cell acquisition. Moreover, this extended accumulation period improves PSC code detection without introducing other errors due to clock frequency drift. 
     Turning now to  FIG. 9 , there is a simulation showing initial cell acquisition time as a function of the base station transmit power-to-noise ratio. The simulation shows three curves representing time in each of stage  1 , stage  2  and stage  3  acquisition. The time Tacc is the time between stage  1  reset signals. For example, curve  900  indicates 10/10/5 corresponding to 10 milliseconds in stage  1 , 10 milliseconds in stage  2  and 5 milliseconds in stage  3 . Tacc for curve  900  is 5 milliseconds. Each second-stage acquisition corresponding to curve  900 , therefore, only accumulates PSC code match values for eight time slots before stage  2 . Alternatively, curve  902  accumulates PSC code match values for 15 milliseconds over twenty-four time slots and shows a significant reduction in acquisition time compared to curve  900 . By way of comparison, curve  904  shows an even greater reduction in initial acquisition time with 20 milliseconds of accumulated PSC code values. 
     The simulation of  FIG. 10  shows a corresponding reduction in cell acquisition time during soft handoff from one base station to another for curves  906 ,  908  and  910 . First-stage PSC code value accumulation for curves  906  and  908  are both 20 millisecond. Curve  908 , however, shows a significant reduction in acquisition time compared to curve  906  due to the 10 millisecond time in stage  1 . A different stage  2  begins every 20 milliseconds for curve  906  and every 10 milliseconds for curve  908 . The greater number of comparisons corresponding to curve  908 , therefore, produces a comparable reduction in cell acquisition time compared to curve  906 . 
     Although the invention has been described in detail with reference to its preferred embodiment, it is to be understood that this description is by way of example only and is not to be construed in a limiting sense. For example, advantages of the present invention may be achieved by a digital signal processing circuit as will be appreciated by those of ordinary skill in the art having access to the instant specification. Moreover, although a preferred embodiment of the present invention teaches diversity information transmission through PSC or SSC symbols, other information such as base station transmit power or system frame number may also be included. Furthermore, these PSC or SSC symbols may also be encoded as QPSK symbols rather than BPSK, thereby doubling the information content of each symbol. 
     It is understood that the inventive concept of the present invention may be embodied in a mobile communication system as well as circuits within the mobile communication system. It is to be further understood that numerous changes in the details of the embodiments of the invention will be apparent to persons of ordinary skill in the art having reference to this description. It is contemplated that such changes and additional embodiments are within the spirit and true scope of the invention as claimed below.