Patent Publication Number: US-9837986-B2

Title: Floating immittance emulator

Description:
CROSS-REFERENCE TO RELATED APPLICATION 
     This application is a divisional of U.S. patent application Ser. No. 14/951,467, filed Nov. 24, 2015, now pending. 
    
    
     BACKGROUND OF THE INVENTION 
     1. Field of the Invention 
     The present invention relates to emulator circuits, particularly to floating immittance emulator circuits that use three current-feedback operational amplifiers (CFOAs). 
     2. Description of the Related Art 
     Over the years researchers have reported several floating inductance simulators using a wide range of active elements. This is attributed to its importance in designing many analog signal processing circuits, such as impedance matching circuits, low frequency filters, and oscillators, where relatively large values of inductance that cannot be fabricated on the chip are required. Of particular interest are realizations based on the use of the CFOA as an active element. This is attributed to the unique characteristics of the CFOA, such as the relatively wider operating bandwidth (there is no gain-bandwidth limitation), its relatively high slew rate, and its commercial availability. Obviously, the use of the minimum number of CFOAs is preferable, as it implies less power consumption and less area on the chip. 
     Thus, a floating immittance emulator solving the aforementioned problems is desired. 
     SUMMARY OF THE INVENTION 
     The floating immittance emulator is presented in various circuits for emulating immittance (impedance or admittance [ratio of current to voltage]; immittance is a term embracing both). Each circuit uses three current-feedback operational-amplifiers (CFOAs), and passive elements. The present topologies can emulate lossless and lossy floating inductances, and capacitance, resistance and inductance multipliers, in addition to frequency-dependent positive and negative resistances. The functionality of the present circuits is verified using Advanced Design System (ADS) software and the AD844 CFOA. The simulation results are in excellent agreement with the theoretical calculations. 
     These and other features of the present invention will become readily apparent upon further review of the following specification and drawings. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         FIG. 1A  is a schematic diagram of a first embodiment of a floating immittance emulator according to the present invention. 
         FIG. 1B  is a schematic diagram of a second embodiment of a floating immittance emulator according to the present invention. 
         FIG. 1C  is a schematic diagram of a third embodiment of a floating immittance emulator according to the present invention. 
         FIG. 1D  is a schematic diagram of a fourth embodiment of a floating immittance emulator according to the present invention. 
         FIG. 2  is a block diagram of a test circuit for the floating immittance emulators of  FIGS. 1A-1D . 
         FIG. 3  is a plot showing the transfer function of a bandpass filter obtained using the inductance emulator of  FIG. 1A   
         FIG. 4  is a plot showing the transfer function of a bandpass filter obtained using the inductance emulator of  FIG. 1B   
         FIG. 5  is a plot showing waveforms of the current through and the voltage across an inductance emulated using  FIG. 1C   
         FIG. 6  is a plot showing the transfer function of a bandpass filter obtained using the immittance emulator of  FIG. 1C   
         FIG. 7  is a plot showing the transfer function of another bandpass filter obtained using the immittance emulator of  FIG. 1C   
         FIG. 8  is a plot showing waveforms of the current through and the voltage across a capacitance emulated using the immittance emulator of  FIG. 1C   
         FIG. 9  is a plot showing variation of the capacitance obtained using a capacitance multiplier emulated using the immittance emulator of  FIG. 1C   
         FIG. 10  is a plot showing variation of the resistance obtained using a resistance multiplier emulated using the immittance emulator of  FIG. 1C . 
         FIG. 12  is a plot showing waveforms of the current through and the voltage 
         FIG. 11  is a plot showing variation of the inductance obtained using the inductance multiplier emulated using the immittance emulator of  FIG. 1C . across a frequency-dependent negative-resistance emulated using the immittance emulator of  FIG. 1C   
         FIG. 13  is a plot showing waveforms of the current through and the input voltage of the circuit built using the negative inductance emulated using the immittance emulator of  FIG. 1D   
     
    
    
     Similar reference characters denote corresponding features consistently throughout the attached drawings. 
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     As shown in  FIGS. 1A, 1B, 1C and 1D , the three-CFOA-based floating immittance emulator includes inductance simulators using three CFOAs. Regarding references to the y, x, z, and w-terminals of the CFOAs, it will be understood that as used herein, the y- and x-terminals are input terminals of a CFOA building block and z- and w-output terminals of the CFOA comprise the z-output terminal (the slewing node of the Analog Devices AD844) and w-output terminal, respectively, of the CFOA. 
     The immittance emulator circuit  100   a  shown in  FIG. 1A  includes a first CFOA  112   a  having first y-, x-, z-, and w-terminals, first z-terminal being connected to ground. A second CFOA  112   b  having second y-, x-, z-, and w-terminals, the second z-terminal being connected to the second y-terminal. A third CFOA  112   c  having third y-, x-, z-, and w-terminals, the third z-terminal being connected to the second x-terminal of the second CFOA. A first impedance  101  has a first lead connected to the first y-terminal of the first CFOA  112   a  and a second lead connected to the third x-terminal of the third CFOA  112   c . A second impedance  102  having a first lead connected to the first x-terminal of first CFOA  112   a  and a second lead connected to the third y-terminal of third CFOA  112   c . A third impedance  103  having a first lead connected to the third y-terminal of third CFOA  112   c  and a second lead connected to the third w-terminal of third CFOA  112   c . This circuit performs immittance emulation between a voltage v 1  applied to the first y-terminal of the first CFOA  112   a  and a voltage v 2  applied to the second y-terminal of the second CFOA  112   b.    
     The immittance emulator circuit  100   b  shown in  FIG. 1B  includes a first CFOA  112   a  having first y-, x-, z-, and w-terminals. A second CFOA  112   b  having second y-, x-, z-, and w-terminals. A third CFOA  112   c  having third y-, x-, z-, and w-terminals, the third z-terminal being connected to the first x-terminal of the first CFOA  112   a . A first impedance  101  has a first lead connected to the first y-terminal of first CFOA  112   a  and a second lead connected to the third x-terminal of third CFOA  112   c . A second impedance  102  has a first lead connected to the third w-terminal of third CFOA  112   c  and a second lead connected to the third y-terminal of third CFOA  112   c . A third impedance  103  has a first lead connected to the third y-terminal of third CFOA  112   c  and a second lead connected to the second x-terminal of second CFOA  112   b . The second z-terminal of the second CFOA  112   b  is connected to ground. The second y-terminal of the second CFOA  112   b  is connected to first z-terminal of CFOA  112   a . This circuit performs immittance emulation between a voltage v 1  applied to the first y-terminal of the first CFOA  112   a  and a voltage v 2  applied to the second y-terminal of the second CFOA  112   b.    
     The immittance emulator circuit  100   c  shown in  FIG. 1C  includes a first CFOA  112   a  having first y-, x-, z-, and w-terminals. A second CFOA  112   b  has second y-, x-, z-, and w-terminals. A third CFOA  112   c  has third y-, x-, z-, and w-terminals, the third z-terminal being connected to the first x-terminal of the first CFOA  112   a , the third y-terminal being connected to the second w-terminal of CFOA  112   b . A first impedance  101  has a first lead connected to the first y-terminal of the first CFOA  112   a  and a second lead connected to the third x-terminal of the third CFOA  112   c . A second impedance  102  has a first lead connected to the third w-terminal of the third CFOA  112   c  and a second lead connected to the second z-terminal of the second CFOA  112   b . A third impedance  103  has a first lead connected to the third w-terminal of the third CFOA  112   c  and a second lead connected to the second x-terminal of the second CFOA  112   b . The second y-terminal of the second CFOA  112   b  is connected to the first z-terminal of CFOA  112   a . This circuit performs immittance emulation between a voltage v 1  applied to the first y-terminal of the first CFOA  112   a  and a voltage v 2  applied to the second y-terminal of the second CFOA  112   b.    
     The immittance emulator circuit  100   d  shown in  FIG. 1D  includes a first CFOA  112   a  having first y-, x-, z-, and w-terminals. A second CFOA  112   b  has second y-, x-, z-, and w-terminals. A third CFOA  112   c  has third y-, x-, z-, and w-terminals, the third x-terminal being connected to the first x-terminal of the first CFOA  112   a  and the second x-terminal of the second CFOA  112   b . A first impedance  101  has a first lead connected to the first y-terminal of the first CFOA  112   a  and a second lead connected to the first z-terminal of the first CFOA  112   a  and the second z-terminal of the second CFOA  112   b . A second impedance  102  has a first lead connected to the first w-terminal of the first CFOA  112   a  and a second lead connected to the third y-terminal of the third CFOA  112   c . A third impedance  103  has a first lead connected to the third y-terminal of the third CFOA  112   c  and a second lead connected to the third w-terminal of the third CFOA  112   c . The second y-terminal of the second CFOA  112   b  is connected to first y-terminal of CFOA  112   a . The second w-terminal of the second CFOA  112   b  is connected to the first w-terminal of CFOA  112   a . This circuit performs immittance emulation between a voltage v 1  applied to the first y-terminal of the first CFOA  112   a  and a voltage v 2  applied to the third z-terminal of the third CFOA  112   c.    
     Assuming that the CFOAs are characterized by v y =v x , i z =i x , v w =v z , i y =0, routine analysis shows that the input impedance between terminals  1  and  2  of  FIGS. 1A-1D  is given by 
                       Z   in     =           V   1     -     V   2         I   in       =       Z   1     +         Z   1     ⁢     Z   3         Z   2             ,           (   1   )               
for the circuits of  FIGS. 1A and 1B ,
 
                       Z   in     =           V   1     -     V   2         I   in       =         Z   1     ⁢     Z   3         Z   2           ,           (   2   )               
for the circuit of  FIG. 1C , and
 
                       Z   in     =           V   1     -     V   2         I   in       =     -         Z   1     ⁢     Z   3         Z   2             ,           (   3   )               
for the circuit of  FIG. 1D .
 
     Thus, with 
                 Z   1     =     R   1       ,       Z   2     =     1     sC   2         ,         
Z 3 =R 3 , then the circuits of  FIGS. 1A and 1B  can simulate a lossy inductance with a series connected resistance with R eq =R 1 , L eq =C 2 R 1 R 3 , the circuit of  FIG. 1C  can simulate a positive lossless inductance with L eq =C 2 R 1 R 3 , and the circuit of  FIG. 1D  can simulate a lossless negative inductance with L eq =−C 2 R 1 R 3 . Moreover, with
 
                 Z   1     =     1     sC   1         ,       Z   3     =     1     sC   3               
and, Z 2 =R 2  the circuit of  FIG. 1C  can simulate a positive frequency dependent resistance given by:
 
               R   eq     =     1       ω   2     ⁢     C   1     ⁢     C   3     ⁢     R   2               
and the circuit of  FIG. 1D  can simulate a negative frequency dependent resistance given by:
 
               R   eq     =         -   1         ω   2     ⁢     C   1     ⁢     C   3     ⁢     R   2         .           
Furthermore, with Z 1 =R 1 , Z 3 =R 3  and Z 2 =R 2 , the circuit of  FIG. 1C  realizes a positive resistance multiplier given by:
 
               R   eq     =         R   1     ⁢     R   3         R   2             
and the circuit of  FIG. 1D  can simulate a negative resistance multiplier given by:
 
               R   eq     =     -           R   1     ⁢     R   3         R   2       .             
Finally, with Z 1 =R 1 , Z 2 =R 2  and
 
                 Z   3     =     1     sC   3         ,         
the circuit of  FIG. 1C  can simulate a positive capacitance multiplier with:
 
               C   eq     =         R   2     ⁢     C   3         R   1             
and the circuit of  FIG. 1D  can simulate a negative capacitance multiplier with:
 
     
       
         
           
             
               C 
               eq 
             
             = 
             
               - 
               
                 
                   
                     
                       R 
                       2 
                     
                     ⁢ 
                     
                       C 
                       3 
                     
                   
                   
                     R 
                     1 
                   
                 
                 . 
               
             
           
         
       
     
     The proposed circuits of  FIGS. 1A, 1B, 1C and 1D  were simulated using the CFOA specified as Analog Devices AD844 with DC supply voltages=±5.0V. The proposed lossy floating positive inductor obtainable from  FIG. 1A  was used in the test bench circuit of  FIG. 2  with Z i  formed of a capacitance C i =1.0 μF and the resistance R o =2.5 kΩ, and the values of the components in  FIG. 1A  selected as R 1 =1.0 kΩ, C 2 =1.0 μF and R 3  as a variable resistor in the range 1.0 kΩ-50.0 kΩ. The output voltage across the resistance R o  was monitored, and the results obtained are shown in  FIG. 3 . Inspection of  FIG. 3  shows that the circuit behaves as a bandpass filter with variable Q and center frequency. Calculations using the simulation results show that the emulated inductance has a loss equivalent to 1.07 kΩ, which agrees well with the theoretical calculation of 1.0 kΩ loss. Moreover, inspection of  FIG. 3  shows that the center frequency varies between 21.0 Hz and 151.0 Hz. This is in excellent agreement with the calculations showing that the center frequency changes from 22.5 to 159.0 Hz. This confirms that the circuit of  FIG. 1A  emulates a lossy positive floating inductance. 
     The proposed lossy floating positive inductor obtainable from  FIG. 1B  was used in the test bench circuit  200  of  FIG. 2  with external impedance Z i  formed of a capacitance C i =1.0 μF and the resistance R o =2.5 kΩ, and the values of the components in  FIG. 1B  selected as R 1 =1.0 kΩ, C 2 =1.0 μF and R 3  variable in the range 1.0 kΩ-50.0 kΩ. The output voltage across the resistance R o  was monitored, and the results obtained are shown in  FIG. 4 . Inspection of  FIG. 4  shows that the circuit behaves as a bandpass filter with variable Q and center frequency. This confirms that the circuit of  FIG. 1A  simulates a lossy positive floating inductance. The simulation results show that the center frequency changes from 22.5 Hz to 159.0 Hz. This is in excellent agreement with the calculations showing that the center frequency changes between 21.0 Hz and 151.0 Hz. 
     The proposed lossless floating positive inductor obtainable from  FIG. 1C  was used in the test bench circuit of  FIG. 2  with Z i  formed of a resistance R i =314Ω and the resistance R o =314Ω, and the values of the components in  FIG. 1C  selected as R 1 =1.0 kΩ, C 2 =50.0 nF and R 3 =1.0 kΩ. The current through the emulated inductance and the voltage across it were monitored, and the results obtained are shown in plot  500  of  FIG. 5 . Inspection of  FIG. 5  shows that the current through the emulated inductance lags by 90° behind the voltage across it. The proposed lossless floating positive inductor obtainable from  FIG. 1C  was also used in the test bench circuit  200  of  FIG. 2  with Z i  formed of a capacitance C i =1.0 μF and resistance R o =1.0 kΩ, and the values of the components in  FIG. 1C  selected as C 2 =1.0 μF, R 3 =1.0 kΩ, and R i  as a variable in the range 1.0 kΩ-50.0 kΩ. The voltage across the resistance R o  was monitored, and the results obtained are shown in plot  600  of  FIG. 6 . Inspection of  FIG. 6  shows that the circuit behaves as a bandpass filter with variable Q and center frequency. This confirms that the circuit of  FIG. 1C  emulates a lossy positive floating inductance. The simulation results show that the center frequency changes from 22.0 Hz to 151.0 Hz. This is in excellent agreement with the calculations showing that the center frequency changes between 22.5 Hz and 159.0 Hz. 
     With the values of the components in  FIG. 1C  selected as C 2 =47.0 μF, R 3 =25.0 kΩ, and R 1  as a variable in the range 9.17 kΩ-50.0 kΩ, the proposed emulated positive inductor was tested using the test bench circuit of  FIG. 2  with C i =4.7 μF and resistance R o =1.0 kΩ, and the voltage across the resistance R o  was monitored. The results obtained are shown in plot  700  of  FIG. 7 . Inspection of  FIG. 7  shows that the circuit behaves as a bandpass filter with variable Q and center frequency. The simulation results show that the center frequency changes in the range 0.303 Hz-0.7075 Hz. This is in excellent agreement with the calculations showing that the center frequency changes in the range 0.3030 Hz-0.7076 Hz. This confirms that the circuit of  FIG. 1C  emulates a lossy positive floating inductance and can be used in designing bandpass filters with center frequencies in the sub-Hz region. 
     The proposed lossless floating positive capacitance obtainable from  FIG. 1C  was used in the test bench circuit of  FIG. 2  with Z i  and Z o  formed of resistances R i =R o =1.0 kΩ and the values of the components in  FIG. 1C  selected as C 1 =1.0 μF, R 2 =10.0 kΩ, and R 3 =1.0 kΩ. The voltage across the emulated capacitor and the current through it were monitored, and the results are shown in plot  800  of  FIG. 8 , where the current is leading the voltage by 90°. This confirms that the circuit  100   c  of  FIG. 1C  emulates a lossless positive capacitance. The proposed circuit  100   c  of  FIG. 1C  was also tested as a capacitance multiplier by connecting it in the test bench circuit  200  of  FIG. 2  with first external impedance  202  Z i  and Z o  (second external impedance  204 ) formed of resistances R i =R o =1.0 kΩ, and the values of the components of circuit  100   c  in  FIG. 1C  selected as C 1 =1.0 nF, R 3 =5.0 kΩ, and R 2  as a variable in the range 10.0 kΩ-65.0 kΩ. The value of the emulated capacitance was monitored, and the results are shown in plot  900  of  FIG. 9 . Inspection of plot  900  of  FIG. 9  clearly shows that with R 2 =20.0 kΩ, the circuit  100   c  of  FIG. 1C  emulates a capacitance=4.175 nF, while the calculated value is C=4.0 nF, and with R 2 =70.0 kΩ, the circuit emulates a capacitance=13.65 nF, while the calculated value is 14.0 nF. Thus, a capacitance multiplication by a factor of 15.0 can be achieved. However, the multiplication factor is not linearly increasing with the value of R 2  for values of R 2 &gt;70.0 kΩ. This may be attributed to the nonidealities of the CFOAs. 
     The proposed circuit  100   c  of  FIG. 1C  was also tested as a resistance multiplier by connecting it in the test bench circuit of  FIG. 2  with Z i  and Z o  formed of resistances R i =R o =1.0 kΩ, and with the values of the components of circuit  100   c  in  FIG. 1C  selected as R 1 =1.0 kΩ, R 2 =1.0 kΩ, and R 3  as a variable in the range 1.0 kΩ-500.0 kΩ. The value of the emulated resistance was monitored, and the results are shown in plot  1000  of  FIG. 10 . Inspection of  FIG. 10  clearly shows that a resistance multiplication by a factor of 500 can be achieved. However, the multiplication factor is not linearly increasing with the value of R 3  for values of R 3 &gt;100.0 kΩ. This may be attributed to the nonidealities of the CFOAs. 
     The proposed circuit of  FIG. 1C  was also tested as an inductance multiplier by connecting it in the test bench circuit of  FIG. 2  with Z i  and Z o  formed of resistances R i =R o =1.0 kΩ, and with the values of the components in  FIG. 1C  selected as L 1 =1.0 mH, R 2 =1.0 kΩ, and R 3  variable in the range 1.0 kΩ-25.0 kΩ. The value of the emulated inductance was monitored, and the results are shown in plot  1100  of  FIG. 11 . Inspection of  FIG. 11  clearly shows that an inductance multiplication factor by 25.0 can be achieved. 
     The proposed circuit of  FIG. 1C  was also tested as a frequency-dependent negative-resistance by connecting it in the test bench circuit of  FIG. 2  with R i =R o =20.0 kΩ, and with the values of the components in  FIG. 1C  selected as R 1 =1.0 kΩ, L 3 =200.0 mH and C 2 =1.0 μF. The voltage across and the current through the emulated frequency-dependent negative-resistance were monitored, and the results are shown in plot  1200  of  FIG. 12 . Inspection of  FIG. 12  clearly shows that the phase shift between the current and the voltage is 180°. This is a clear indication that the circuit is emulating a negative resistance. Moreover, at frequency=2 kHz, the calculated negative resistance is 31.55 kΩ, which is in excellent agreement with the simulated value of 29.956 kΩ. 
     The proposed negative lossless floating inductor obtainable from  FIG. 1D  was used in the test bench circuit of  FIG. 2  with Z i  formed of a variable positive inductance (L i ) and Z o  formed of resistance (R o ). With the inductance L i  varying in the range 54.5 mH-60.0 mH, and the resistance R o =500Ω, and the values of the components in  FIG. 1D  selected as R 1 =1.0 kΩ, R 3 =1.0 kΩ and C 2 =50 nF to emulate a lossless negative inductance=−50 mH, the applied input voltage and the resulting current though the circuit  200  of  FIG. 2  were monitored. The results obtained are shown in plot  1300  of  FIG. 13 . Inspection of  FIG. 13  clearly shows that the current through the circuit and the applied input voltage are in phase, indicating that the total impedance is purely resistive only when the externally connected inductance is equal to 54.5 mH. Otherwise, the current and the voltage are not in phase, indicating that the total impedance is inductive. This confirms that the proposed circuit of  FIG. 1D  emulates a negative inductance=−54.5 mH, with an error equal to 9.5% between the calculated and simulated values. 
     A catalog comprising four new circuits for emulating immittance functions has been presented. Each circuit uses three CFOAs and three passive elements. Using a test bench circuit, the proposed circuits were tested for realizing bandpass filters; capacitance, resistance, and inductance multipliers; and cancellation of positive inductances and resistances. The results show that bandpass filters working in the sub-Hz region are obtainable, and cancellation of positive inductances and resistances is feasible. The simulation results obtained are in excellent agreement with the calculations. The maximum error obtained is 9.5% for the case of emulating a negative inductance. For large values of a multiplying factor, in the case of resistance, capacitance and inductance multipliers, the multiplying factor exhibits a slight nonlinearity. This is attributed to the nonideal characteristics of the CFOAs. Moreover, the proposed emulators do not require any matching conditions. 
     It is to be understood that the present invention is not limited to the embodiments described above, but encompasses any and all embodiments within the scope of the following claims.