Patent Document

BACKGROUND OF THE INVENTION 
       [0001]    1. Field of the Invention 
         [0002]    The present invention relates to a system or a method for measuring flow of fluid or gas, which system comprises a flow duct, which flow duct comprises at least two transducers, which transducers generate at least one beam of ultrasound in the flow duct, which Transmitter/receiver circuits are connecting through a transmitter/receiver switch, which switch in a first position connect first Transmitter/receiver circuit to a transmitter circuit and second transducers are connected to a receiver circuit, which receiver circuit comprises at least a band pass filter, which band pass filter is further connected to a microcontroller, which microcontroller comprises an analogue to digital converter, which digital converter converts the analogue signal into digital data samples representing at least transit times and time difference, which microcontroller stores the data samples in a memory. 
         [0003]    2. Description of Related Art 
         [0004]    International Patent Application Publication WO 2010/122117 discloses a ventilation system, wherein a fan draws air from an exterior of a building or similar closed construction for circulation into an interior of the building, and produces supply airflow through a ventilator unit, which is able to cool and heat air. Moreover, the ventilator unit may be equipped with a humidifying/dehumidifying device. A controller controls the position of a valve or indirectly the speed of the fan, thereby adjusting the supply airflow in response to an input received from an ultrasound device placed in the supply air duct, wherein the ultrasound device measures the air flow and temperature. 
       SUMMARY OF THE INVENTION 
       [0005]    It is a primary object of the present application to measure the flow of air in a duct by one or more transducers transmitting beams of ultra sound controlled by a microcontroller based electronic system. 
         [0006]    The object can be achieved if the transmitter circuit and a receiver circuit are controlled by a switch, which switch perform continuous switching of transmitter circuit into a receiver circuit and the receiver circuit into a transmitter circuit, which microcontroller stores a vector of data samples for each direction of transmission, which vector comprises an appropriate number of N samples forming a frame, which microcontroller multiplies each value of the frame which is a complex number with the magnitude one and a phases representing the transmitted frequency and phase, which microprocessor generates imaginary values and a real values, which imaginary values and a real values low pass filtrated in a digital filter, which filtrated values are sent to an amplitude function and to a phase detection function, which microcontroller based on the result of the amplitude function and the result of the phase detection function calculates the flow in the duct. 
         [0007]    In accordance with the invention of the present patent application, an efficient flow measurement of air flowing in a duct is achieved. It is realized that the damping of signals between two transducers in air is sufficiently higher than the damping that is found in traditional ultrasound flow measuring systems simply because a liquid is better matched to the impedance of the transducers. Because of the relatively weak and long signals that are transmitted and received, it is necessary to isolate the receiver from the transmitter in order to get good results of the signals received. By treating the received signals as an oscillating signal which has a curve form which is mostly a sinus curve it is possible to handle that sinus form mathematically and to divide it into the imaginary and real parts of the signal. This can lead to a situation where the amplitude can be very accurately detected, but also very precise phase detection can be made. By performing an efficient low pass filtration of the signals, it is achieved that all signals having higher frequencies are reduced so their influence on the measurement is non-existant. This can lead to a much higher precision of the measured signals. 
         [0008]    The result of the amplitude function can further be processed by the microcontroller in a digital constant fraction discriminator (CFD). Hereby, it is achieved that arrival times T UP  and T DWN  are measured by the constant fraction discriminator. The output from the CFD is used to place the sampling frame so it preferably starts where the pulse would have been if there had been no dead delay. The dead delay is the delay due to signal transmissions through cables and influence from solid parts of the transducers and also if there is a delay in one of the end filters used. The start of the sampling frame can partially equal the transmission time in the air T UP  and T DWN . The frequency of the time clock will limit the resolution, but the precision is sufficient for the T UP  and T DWN  values in the denominator, but not sufficient for the various delta-Ts since this requires a higher resolution than that by which the sampling frame is adjusted. 
         [0009]    The result of the phase detection function can further be processed by the microcontroller in a digital signal representing the time shift relative to the frame. Hereby, an increase is achieved of the resolution of the time difference T UP −T DWN =ΔT. Hereby, highly efficient phase detection can be performed. Hereby, a relative decrease can be achieved in standard deviations with the above method compared to the deviation obtained from a zero-crossing detection of the same signal as that known from the prior art. 
         [0010]    The system comprises a transmitter circuit comprising a band pass amplifier to limit the bandwidth of a transmission burst from the microcontroller, which band pass amplifier transmits a signal through the switch, and further, to one of the transducers. Hereby, it is achieved that the band pass amplifier can limit the band width of the transmission first from the microcontroller. Signals generated by the microcontroller do have a high slew rate That high slew rate must be reduced in order not to overload the transmitting amplifiers because these amplifiers have a maximum slew rate to which the slew rate of the output signal becomes limited. With the amplifiers in an active state, it can be achieved that the transducers are connected to the same node in the circuit, both during transmission and reception, and are always loaded with the same impedance. 
         [0011]    The system comprises a transducer amplifier, which transducer amplifier connects the transducer to the same node in the circuit both during transmission and reception. The transducer amplifier comprises a voltage follower. Hereby, it can be achieved that the voltage on the positive input terminal is followed by the negative input terminal, and if a signal appears on the negative input terminal, it is amplified and inverted on the output of the amplifier. When the amplifier is used for transmitting the signal, the amplifier is a power amplifier of a large signals, and when receiving the amplifier acts as a pre-amplifier of small signals. The diodes coupled anti-parallel over the feedback resistor prevents the amplifier output from becoming into saturation and allow for appropriate amplification of the received signal. 
         [0012]    The system comprises at least one transmitter receiver switch, which transmitter receiver switch comprises at least three contacts by which contacts that are not used terminals are ground connected for reducing noise. Hereby, it is achieved that an extra switch is coupled between the contacts in the first switch and perform capacitive coupling to the ground instead of the transmission signal from the other channel. This is especially important in air transducers where the received signal is normally 60 dB lower than the transmitted signal and the transmitting transducer continues ringing for a long time after excitation. 
         [0013]    In a preferred embodiment for the invention, the band pass amplifier comprises automatic gain control, which automatic gain control comprises an operational amplifier connected with a variable feed back resistance, which feed back resistance is controlled by the microcontroller. Hereby, it is achieved that not only the band width is reduced by the band pass filtration, but also the gain control of the signal is under control. Depending on reflection or non-reflection or depending on the diameter of the duct, or maybe the change from one type of transducer to another type, there can be an extremely high difference in signal level that is received. Highly efficient transducers in a very small duct can produce a relatively good signal even in air, but in a different situation where the diameter of the tube is much higher, and maybe a rather less efficient transducer is used, the damping of the signal can be several thousands times, and a much higher amplification is necessary. Only in this way, it can be achieved that analog digital conversion can be made in a perfect way. The upper frequencies are limited to half the sampling frequency of the digital converter, and the gain has to be controlled so that also the signal level is inside the level for the digital conversion. 
         [0014]    The present patent application further concerns a method for operating a system for measuring flow of fluid or gas, as previous disclosed, which method concerns the following steps of operation: 
         [0015]    a: generating at least one beam of ultrasound in the flow duct by a transmitter circuit connected to a first transmission transducer, 
         [0016]    b: receiving the beam of ultrasound in the flow duct by the second transducer and the receiver circuit, 
         [0017]    c: performing a band pass filtration of the received analog signal in the receiver circuit, 
         [0018]    d: converting the analog signal in a digital signal in the microprocessor into digital data samples representing at least transit times and time difference, 
         [0019]    e: storing the data samples in a memory, 
         [0020]    f: storing a vector of data samples for each direction of transmission, 
         [0021]    g: forming a frame based on the vector comprising an appropriate number of N samples, 
         [0022]    h: multiplying each value of the frame with a complex number with the magnitude one and a phase for representing the transmitted frequency and phase, 
         [0023]    i: generating imaginary values and a real values, which imaginary values and real values are low pass filtered in a digital filter, 
         [0024]    j: sending the filtered digital signal to an amplitude function and to a phase detection function, and 
         [0025]    k: calculating the flow in the duct based on the result of the amplitude function and the result of the phase detection function. 
         [0026]    By this method, a very efficient flow measurement in an air duct is achieved. Transducers can be placed across the duct, they can be placed so that reflection takes place, or they can be placed inside the duct so that the transmission of sound is effected directly between the transducers. By the invention according to the present application, it can be achieved that relatively simple and inexpensive transducers can be applied. Therefore, by the invention according to the present application, it is possible to achieve an inexpensive, but yet highly efficient system for measuring air flow. 
     
    
     
       BRIEF DESCRIPTION OF THE DRAWING 
         [0027]      FIG. 1  shows a possible embodiment of the invention. 
           [0028]      FIG. 2  shows a first alternative embodiment of the invention. 
           [0029]      FIG. 3  shows a schematic diagram of the various technical features necessary for computer analysis of received signals. 
           [0030]      FIG. 4  shows a digital constant fraction discriminator CFD. 
           [0031]      FIG. 5  shows a pre-amplifying system connected to the transducers. 
           [0032]      FIG. 6  shows a possible embodiment of an amplifier used as both a transmitter and a receiver. 
           [0033]      FIG. 7  shows a possible embodiment of a switch. 
           [0034]      FIG. 8  shows a possible embodiment of an automatic gain control. 
           [0035]      FIG. 9  shows an alternative embodiment of an automatic gain control. 
           [0036]      FIG. 10  shows a plot of the relation of gain vs. binary digits 
           [0037]      FIG. 11  shows a possible embodiment of a transducer. 
           [0038]      FIG. 12  shows a transducer placed in housing. 
           [0039]      FIG. 13  shows a possible embodiment of a reflective system with two transducers and a reflecting mirror. 
           [0040]      FIG. 14  shows examples of for illustrating disadvantages of the reflecting system. 
           [0041]      FIG. 15  shows alternative embodiment with reflections. 
       
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
       [0042]      FIG. 1  shows a system  2  which system comprises a flow duct  4  in which a first transducer  6  and a second transducer  8  are transmitting acoustic waves  10  across the duct  4 . Both transducers  6 ,  8  are connected to a switch  12  by which switching for receiving and transmission is effected. The transmitter receiver switch  12  is connected to a transmitter circuit  14  and to a receiver circuit  16 . The receiver circuit  16  comprises a band pass filter  18  which is connected to a microcontroller  20 , and the microcontroller  20  is connected to a digital converter  22 . The microcontroller  20  further comprises a digital filter  38 , an amplitude function  42  and a phase detection function  44 . The microcontroller  20  further comprises a digital constant fraction discriminator  46 . Additionally, a voltage follower  50  is shown in the microcontroller  20 . The microcontroller  20  is also connected to the transmitter circuit  14  which comprises a band pass amplifier  48 . 
         [0043]    In operation, flow will be measured between the transducers  6 ,  8 , and in one situation, the transducer  6  acts as transmitter and the transducer  8  acts as receiver, and in the next situation, the transmission occurs in the opposite direction with the transducer  6  acting as the receiver and the transducer  8  as the transmitter. On the basis of these signals, and by the means provided inside the microcontroller  20 , the system can calculate the flow in a highly efficient manner. 
         [0044]      FIGS. 2 &amp; 3  show that the received and band pass amplified signal is analog to digital converted by a built-in analog to digital converter and is stored in memory. The measurements of transit times and time difference are solely performed by the microcontroller  120  based on these stored values. 
         [0045]    After transmission in either direction, a number of samples are stored in the memory. The sampling starts after a time determined by an internal timer in the microcontroller  120  such that the received pulse is sampled from the beginning. The time for the first sample is stored in the memory as one value for transmission against the flow and another value for transmission with the flow. 
         [0046]    A vector of samples is stored for each direction of transmission. Each vector contains an appropriate number N of samples, in the actual embodiment the vector  130  contains 512 samples, but less may work well. 
         [0047]    The first step in the signal processing is to multiply each value in the frames with a complex number with the magnitude one and a phase corresponding to the transmitted signal: 
         [0000]        Y   n   =X   n   ·e   jω·t     s     ·n   =X   n ·(cos(ω· t   s   ·n )+ j  sin(ω· t   s   ·n ))  164
 
         [0048]    Where X n  is the stored value at the n th  location, jω the angular frequency of the transmitted signal, t s  the sampling time interval and n is the sample number. 0≦n&lt;N The complex result Y n  is filtered by two low pass filters, one for the real part a n  and one for the imaginary part b n . 
         [0049]    After low pass filtering,  116   im ,  116   re  is the result is a complex sequence (a n +jb n ) with n={0, 1, . . . N-1, N}. The amplitude 142 of the received signal can, sample for sample, be found as the square root of the sum of squares. 
         [0000]        A   n =√{square root over ( a   n   2   +b   n   2 )}  142
 
         [0050]      FIG. 4  shows a possible embodiment for an amplitude signal that is used to determine the arrival times T UP  and T dwn  by means of a digital constant fraction discriminator CFD  146 . 
         [0051]    The output from the CFD  146  is used to place the sampling frame so that it starts where the pulse would have been if there has been no dead delay. The dead delay is the delay due to cables, solid parts of transducers and delay in the band pass filter. The start of the sampling frame ideally equals the transmission time in the fluid T UP  and T dwn . The frequency of the timer clock limits the resolution, but the precision is sufficient for the T UP  and T dwn  values in the denominator, but not sufficient for the difference Δt since it requires more resolution than the sampling frames are adjusted with. 
         [0052]    The purpose of the phase detection  144  is to increase the resolution of the time difference T UP −T dwn =Δt. The output from the low pass filters  116   im ,  116   re  represents the phase difference between the frame with its reference sequence and the received signal. The filtered output can be further filtered to decrease the standard deviation on the phase measurements. The phase is the argument to the last complex number (a N-1 +jb N-1 ) in the vector  130  where the amplitude and phase are stable. 
         [0053]    If the signal from the upstream measurement is (a N-1 +jb N-1 ) and from the downstream measurement is (c N-1 +jd N-1 ), then the phase difference is: 
         [0000]    
       
         
           
             
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         [0000]    The argument can be found as shown below: 
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         [0054]    Since the angle is small if the frame is adjusted with steps much smaller than the sample time the arctan is easily calculated by the series: 
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         [0055]    The actual length of the series depends on the required accuracy and the range of values of x, but the shown length will normally suffice. 
         [0056]    If noise is present, the CFD signal  146  may fluctuate with a few samples and the nominal value of the division may be larger than the range of the arc tan function, but a few numbers out of range can be discarded without offsetting the mean value of measurements since the deviations are expected to be symmetrical. 
         [0057]    Practical measurements have shown a three to five times decrease in standard deviation with the above method compared to the deviations obtained from a zero crossing detection on the same signal. 
         [0058]    The band pass amplifier is necessary to limit the bandwidth of the transmission burst from the microcontroller. A square wave like the burst from the microcontroller has too a high slew rate which will bring the operational amplifier in the T/R switch  112  into slew rate limit and ruin the essential reciprocity of the T/R switch  112 . 
         [0059]    The transducer amplifiers can be coupled as voltage followers  150  or as current generators. 
         [0060]    A main difference from common practice is that the transducer is connected to a node in the circuit without switches, the input of the transmission signal to another and the received signal appears on a third. The transducer is connected to the same node in the circuit both during transmission and reception, and thus, is always loaded with the same impedance. As a result, it obeys the “reciprocity theorem” making the time delay difference (difference in transmission time with or against the flow) unchanged by transducer changes due to temperature, contamination or aging. 
         [0061]      FIG. 5  shows a possible embodiment for an amplifier circuit for connoting the transducers  206 ,  208 . The voltage on the positive input terminal of one of the operational amplifiers  214 ,  216  is followed by the negative input terminal, and if a signal appears on the negative terminal, it is amplified and inverted on the output of the amplifier  214 ,  216 . When the amplifier  214 ,  216  is used for transmitting a signal, the amplifier  214 ,  216  is a “power amplifier” of a large signal, and when receiving, the amplifier acts as a preamplifier of a small signal. The anti-parallel diodes  260 ,  262  serve as low impedance during transmission and as high impedance during receive mode preventing the amplifier  214 ,  216  from going into saturation under transmission of a large signal. Under reception of small signals they act virtually as disconnections compared to the resistor they are parallel to. 
         [0062]    The reciprocity theorem requires the transmitting transducer to be driven with the same impedance as the transducer used as receiver. In  FIG. 5 , the impedances are virtually zero, but any impedance can be used. 
         [0063]    The circuit in  FIG. 6  has virtually infinite impedances as a current generator, both as power amplifier and as preamplifier. 
         [0064]    In principle, the T/R switch  312  of  FIG. 7  can look like in  FIG. 5 . But in most cases, it is too simple. In practice, a more elaborate scheme must be followed to avoid over coupling of the transmission signal via the off capacitance of the switch  312 . An example of minimizing the influence of the off capacitance in the switch is shown in  FIG. 7 . 
         [0065]    An extra switch  314 ,  316  is provided enable a capacitive coupling to ground  318 ,  320  instead of to the transmission signal from the other channel. This is especially important in air transducers where the received signal is normally 60 dB lower than the transmitted signal and the transmitting transducer continues “ringing” long time after the excitation. 
         [0066]      FIG. 8  shows a band pass amplifier  402  with AGC. The signal  404  from the front end is for air transducers in the range of few millivolts and hence too small to be analog to digital converted by the built-in analog to digital converters in standard microcontrollers. At the same time, the sampling rate with present technology of low cost microcontrollers is in the range of 1 to 2 million samples per second. In order to avoid aliasing, all frequencies above half the sampling frequency must be removed before digitizing. The frequencies used in air flow meters are up to 250 kHz, and if 500 kHz shall be damped to say 60 dB, it requires a low pass filter with a very sharp cutoff or a more than 10 th  order filter. 
         [0067]    Alternatively and much better, is a band-pass filter. The required bandwidth is 5 to 10 kHz depending of the transducer used. Sallen-Key or multiple feedback active filters are appropriate, but other filter types, such as passive LC filters, switched capacitor filters or even mechanical filters can be used. 
         [0068]    Due to fabrication tolerances and temperature variation, the signal amplitude will change from transducer to transducer and during operation. In order to minimize the digitizing noise, the analog to digital converter will utilize the full dynamic range, so that the controller will be able to adjust the amplification. In order to keep the dynamic range of the analog to digital converter utilized, the amplification must be changed in appropriate small steps, preferably in a converter, within certain limits, the AGC will work in a way that gives the same percentage gain increase per step. Depending on the gain variation, the necessary number of steps and the size of each step will be chosen. 
         [0069]    A simple 1 of 8 multiplexer 4051 type number can do the task by selecting feedback resistance  406  in an amplifier as shown  FIG. 8   
         [0070]    If larger gain variation is necessary due to the same electronic unit be used for many different tube diameters, or if there exists a possibility for contamination that may dampen the signal, a digital resistor  406  with 1024 steps may be preferred. Since the steps are linear in most commercial versions, a scheme like the one shown in  FIG. 9  may be used. 
         [0071]    This circuit gives a total gain variation of nearly 30 dB distributed over the 1024 steps as shown hereunder: 
         [0072]      FIG. 10  shows a graph that indicates the correlation between the gain and the binary digits. As can be seen from the curvature, increasing binary numbers will achieve a much better gain. 
         [0073]    By using an analog signal from either a digital to analog output or a filtered pulse width or rate modulated signal from the processor analog variable gain amplifiers or circuits with diodes or voltage dependent resistors can be used. Also, use of PTC resistor circuits or the like that thermally changes attenuation on high signal amplitude may be used. 
         [0074]      FIG. 11  discloses the preferred transducers which are common piezoelectric transducers with a piezoelectric element  604  exited at the lowest radial resonance frequency and approximately a quarter wavelength silicon rubber disk  606  as impedance alignment is glued to the front surface of the piezoelectric element  604 . 
         [0075]    Alternatively, transducers used for parking sensors in cars can be used. These normally work at 40 kHz and have a wide angle transmission pattern. If these are used only direct transmission between transducer are used, due to the risk of direct transmission of a spurious signal during the transmission of the reflected signal. 
         [0076]      FIG. 12  shows a possible embodiment for a transducer and transducer housing with the following characteristics, for example. 
         [0000]    
       
         
               
               
               
             
           
               
                   
                   
               
             
             
               
                   
                 608 
                 Transducer housing 
               
               
                   
                 610 
                 Silicon rubber foam (1.5 mm 6 × 58.5) 
               
               
                   
                 604 
                 Silicon rubber foam (1.5 mm Ø 16) 
               
               
                   
                 612 
                 Silicon rubber foam (1.5 mm Ø 20) 
               
               
                   
                 606 
                 PZT (2 × Ø15.5) 
               
               
                   
                 614 
                 Silicon rubber (1,6 × Ø 16) 
               
               
                   
                 616 
                 Metal screen (solder able) 
               
               
                   
                 618 
                 Screened cable 
               
               
                   
                   
               
             
          
         
       
     
         [0077]    While the embodiment is shown in  FIG. 12  is preferred, other forms either preformed or molded in pace may be used. 
         [0078]    Since the sound more readily goes through solids than through air, the transducer must be isolated acoustically from the duct  4 ,  104 , otherwise some sound would be transmitted through the tube wall and arrive at the receiving transducer  6 ,  8 ,  106 ,  108 , and interfere with the flow signal and create nonlinearity. The isolation can be performed with a silicon rubber foam parts  610 ,  604  and  612  in the  FIG. 12 . The material of the the impedance alignment disk can be various other materials with low acoustic impedances and loss, e.g., resin filled with hollow glass spheres or hard foams. 
         [0079]      FIG. 13  shows a flow duct  704  with a reflection  710  whereby the two transducers  706 ,  708  become placed on same side next to each other. The distance between the transducers is the same for all tube diameters; as a result, the time difference Δt for the same flow and temperature becomes the same for all sizes. 
       Sensitivity of the Flow Duct 
       [0080]    Let C be the sound velocity, D the tube diameter, and Lx the distance between the transducers. 
         [0081]    Transducers alternately transmit ultrasonic pulses and alternately receive said transmitted pulses. Thus, the transmission goes with the flow and against it alternately. 
         [0082]    By Pythagoras, the expressions can be written: 
         [0000]      ( C·T   UP ) 2 =(2+ D ) 2 +( Lx+V·T   UP ) 2  and ( C·T   DWN ) 2 =(2+ D ) 2 +( Lx−V·T   DWN ) 2    
         [0083]    First, solve both equations for C and set the results equal to each other and solve for V: 
         [0000]    
       
         
           
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                       4 
                       · 
                       
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                         2 
                       
                     
                     + 
                     
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                       2 
                     
                   
                   
                     2 
                     · 
                     Lx 
                   
                 
                 · 
                 
                   ( 
                   
                     
                       
                         T 
                         UP 
                       
                       - 
                       
                         T 
                         DWN 
                       
                     
                     
                       
                         T 
                         UP 
                       
                       · 
                       
                         T 
                         DWN 
                       
                     
                   
                   ) 
                 
               
                
               
                   
               
                
               or 
             
           
         
       
       
         
           
             Vx 
             = 
             
               
                 
                   
                     4 
                     · 
                     
                       D 
                       2 
                     
                   
                   + 
                   
                     Lx 
                     2 
                   
                 
                 
                   2 
                   · 
                   Lx 
                 
               
               · 
               
                 ( 
                 
                   
                     Δ 
                      
                     
                         
                     
                      
                     t 
                   
                   
                     
                       T 
                       UP 
                     
                     · 
                     
                       T 
                       DWN 
                     
                   
                 
                 ) 
               
             
           
         
       
     
         [0084]    Where Δt is equal to T UP -T DWN  and is found with high precision due to the coherent detection principle. 
         [0085]    Benefits with the reflection in the flow duct configuration: 
         [0086]    The flow meter will be inserted in tubes with nominal bore according to standards. Thus, from T UP  and T DWN  it can be determined which standard diameter the flow meter is inserted in and the appropriate calibration constant can be selected from a table stored in memory. 
         [0087]    Since sound traverses the diameter twice in opposite directions, secondary flow orthogonal to tube axis is partially canceled, so that some common flow disturbances have limited influence. The flow profile due to laminar and turbulent flow does have influence, but since the fluid always is air, the Reynold number influence can be compensated for by a calculation based on T UP  and T DWN . 
         [0088]    The shift from laminar to turbulent flow creates a known shift in flow profile and the shift appears when the Reynolds number is:
       laminar when Re&lt;2300   transient when 2300&lt;Re&lt;4000   turbulent when Re&gt;4000
 
Reynolds number Re is:
       
 
         [0000]    
       
         
           
             Re 
             = 
             
               
                 ρ 
                 · 
                 
                   d 
                   h 
                 
               
               v 
             
           
         
       
     
         [0000]    ρ is the density of air: 
         [0000]    
       
         
           
             ρ 
             = 
             
               p 
               
                 R 
                 · 
                 T 
               
             
           
         
       
     
         [0092]    Where p is the pressure in pascal, R=287.05 J/(kg·K) the specific gas constant and T the temperature in kelvin. (The density for this purpose can be assumed to be 1.2 kg/m 3 ), d h  is the hydraulic diameter of the pipe and v is the kinematic viscosity of air. 
         [0000]    
       
         
           
             v 
             = 
             
               
                 
                   ( 
                   
                     
                       0.0002 
                       · 
                       
                         T 
                         K 
                         2 
                       
                     
                     + 
                     
                       0 
                        
                       
                         , 
                       
                        
                       
                         0053 
                         · 
                         
                           T 
                           K 
                         
                       
                     
                     - 
                     0.0327 
                   
                   ) 
                 
                 · 
                 
                   10 
                   
                     - 
                     6 
                   
                 
               
                
               
                 
                   m 
                   1 
                   2 
                 
                 s 
               
             
           
         
       
     
         [0093]    Where T K  is temperature in kelvin. 
         [0094]    The necessary correction will be determined for each dimension by flow tests, but there exists theoretical/empirical formulas for corrections. 
         [0095]    By these measures it is possible to minimize deviations to a few percent even with flow disturbances as close as a few diameters from the inlet. 
         [0096]    For two reflections, two parabolic mirrors will be used and for three reflections two parabolic and one flat mirror preferably will be used. 
         [0097]    Normal direct transmission with one or more tracks is possible and will be used as an alternative. The calibration constants of this are found by standard well proven principles.

Technology Category: 3