Patent Document

BACKGROUND 
     1. Field of the Invention 
     The present invention relates to techniques for communicating data through a communication channel. More specifically, the present invention relates to a method and apparatus for compensating for frequency dependent losses when transmitting signals through a lossy communication channel. 
     2. Related Art 
     Advances in semiconductor fabrication technology presently make it possible to integrate large-scale systems, including tens of millions of transistors, into a single semiconductor chip. Integrating such large-scale systems onto a single semiconductor chip enables increases in the frequency at which such systems can operate, because signals between system components do not have to cross chip boundaries, and are not subject to lengthy chip-to-chip propagation delays. 
     However, as the frequency of these systems increases, the communication channels used to transfer data between system components is rapidly becoming a bottleneck. At higher frequencies, a communication channel tends to attenuate the transmitted signal. Consequently, if the system transmits data through the communication channel at a sufficiently high frequency, data can be lost. 
     System designers often use voltage-mode drivers to transmit data through communication channels. In order to overcome the frequency dependent signal attenuation problem, some voltage-mode drivers perform a “pre-compensation” operation for higher frequency events to compensate for signal loss. This is accomplished by temporarily boosting the drive strength for high frequency events. Unfortunately, boosting the drive strength in a voltage-mode driver also involves decreasing the source resistance of the driver, which can cause an impedance mismatch with the characteristic impedance of the communication channel. 
     Voltage-mode drivers typically have a drive-strength which is inversely proportional to the source resistance. Therefore, once the source resistance of the voltage-mode driver is set to match the impedance of the communication channel, the drive-strength of the voltage-mode driver is fixed. Hence, a voltage-mode driver cannot compensate for these frequency-dependent losses without causing a corresponding impedance mismatch. 
     One solution to this problem is to use a current-mode driver which has a source resistance that matches the line impedance of the communication channel. The drive strength of a current-mode driver can be boosted by increasing the current, without changing the source resistance. Unfortunately, a current-mode driver uses significantly more power than the voltage-mode driver, which makes such drivers impractical for many applications. 
     Hence, what is needed is a method and an apparatus for increasing the data transfer rate through a communication channel without the problems described above. 
     SUMMARY 
     One embodiment of the present invention provides a system that transmits signals through a communication channel. During operation, the system receives a sequence of bits for transmission through the communication channel. While transmitting a given bit, the system determines if the given bit has the same state as the previously transmitted bit. If so, the system uses a voltage-mode driver to drive a signal through the communication channel. Otherwise, the system uses a current source coupled to the voltage-mode driver to boost the drive-level of the voltage-mode driver. Note that the current source supplies a current to the communication channel without changing the impedance of the voltage-mode driver. In this way, the present invention compensates for frequency dependant losses in the communication channel without sacrificing impedance matching and without substantially increasing power consumption. Note that this configuration saves power because the current source does not consume any power when it is turned off (i.e. when the given bit is the same as the previously transmitted bit). 
     In a variation on this embodiment, the current source is activated independently from the voltage-mode driver, thereby facilitating the optimization of the shape of the transmitted signal. 
     In a variation on this embodiment, more than one current source is used to compensate for frequency dependant losses in the communication channel. Furthermore, each current source is activated separately from the other current sources as well as the voltage-mode driver, thereby facilitating the optimization of the shape of the transmitted signal. 
     In a variation on this embodiment, a sequence of previously transmitted bits is used to control the current source to compensate for the frequency dependant losses in the communication channel. 
     In a variation on this embodiment, the voltage-mode driver is a differential driver. 
     In a variation on this embodiment, the impedance of the voltage-mode driver substantially equals the impedance of the communication channel. 
    
    
     
       BRIEF DESCRIPTION OF THE FIGURES 
         FIG. 1A  presents a block diagram of a voltage-mode driver. 
         FIG. 1B  presents a block diagram of voltage-mode drivers configured for differential-mode operation. 
         FIG. 2A  presents a block diagram of a current-mode driver. 
         FIG. 2B  presents a block diagram of current-mode drivers configured for differential-mode operation. 
         FIG. 3A  illustrates an idealized voltage-versus-time plot of a signal after transmission through a lossy communication channel. 
         FIG. 3B  illustrates an idealized voltage-versus-time plot of a signal after transmission through a lossy communication channel using a current source to boost the drive-level of a voltage-mode driver. 
         FIG. 4  presents a block diagram of a current source coupled to a voltage-mode driver in accordance with an embodiment of the present invention. 
         FIG. 5  presents a block diagram of a current source coupled to a voltage-mode driver configured for differential-mode operation in accordance with an embodiment of the present invention. 
         FIG. 6  presents a block diagram of multiple current source used to optimize the shape of the transmitted signal in accordance with an embodiment of the present invention. 
         FIG. 7  presents a flow chart illustrating process of activating the current source to boost the drive-level of a voltage-mode driver in accordance with an embodiment of the present invention. 
     
    
    
     DETAILED DESCRIPTION 
     The following description is presented to enable any person skilled in the art to make and use the invention, and is provided in the context of a particular application and its requirements. Various modifications to the disclosed embodiments will be readily apparent to those skilled in the art, and the general principles defined herein may be applied to other embodiments and applications without departing from the spirit and scope of the present invention. Thus, the present invention is not limited to the embodiments shown, but is to be accorded the widest scope consistent with the principles and features disclosed herein. 
     Voltage-Mode Drivers 
       FIG. 1A  presents a block diagram of a voltage-mode driver. It contains pull-up network  102 , pull-down network  104 , communication channel  106 , switches  108  and  112 , variable resistors  110  and  114 , termination  116 , and control signal  118 . 
     When the voltage-mode driver transmits a high bit, control signal  118  closes switch  108  and current flows from the power supply, through variable resistor  110  to charge up communication channel  106 . Note that switch  112  remains open when transmitting a high bit. Similarly, when the voltage-mode driver transmits a low bit, control signal  118  closes switch  112  and current flows from the communication channel, through variable resistor  114  to ground. Note that switch  108  remains open when transmitting a high bit. 
     Note that pull-up network  102  and pull-down network  104  can be implemented in any semiconductor technology, including: CMOS, biCMOS, GaAs, etc. In a standard CMOS process, the pull-up network includes a PMOS transistor and the pull-down network includes a NMOS transistor. Note that more than one PMOS and more than one NMOS transistor can be used in the voltage-mode driver. 
     In one embodiment of the present invention, the voltage-mode driver drives the voltage on the communication channel to half of the supply voltage (i.e. VDD/2). Note that VDD is the positive power supply. 
     In high-speed communications and applications where noise is a concern, the voltage-mode drivers are configured for differential-mode operation.  FIG. 1B  presents a block diagram of voltage-mode drivers configured for differential-mode operation. It contains pull-up networks  120  and  132 , pull-down networks  122  and  134 , switches  126 ,  128 ,  138 , and  140 , communication channels  124  and  136 , control signals  130  and  142 , and bridge-tied load  144 . 
     When the differential voltage-mode driver transmits a high bit, control signal  130  closes switch  126  and leaves switch  128  open. Control signal  142  closes switch  140  and leaves switch  138  open. Current flows from the power supply in pull-up network  120 , through communication channel  124 , through bridge-tied load  144 , through communication channel  136 , and to ground in pull-down network  134 . 
     Similarly, when the differential voltage-mode driver transmits a low bit, control signal  130  closes switch  128  and leaves switch  126  open. Control signal  142  closes switch  138  and leaves switch  140  open. Current flows from the power supply in pull-up network  132 , through communication channel  136 , through bridge-tied load  144 , through communication channel  124 , and to ground in pull-down network  122 . 
     Note that the system can alternatively be configured so that the current flows in the opposite direction. For instance, when transmitting a high bit, control signal  130  closes switch  128  and leaves switch  126  open. Control signal  142  closes switch  138  and leaves switch  140  open. Therefore, current flows from the power supply in pull-up network  132 , through communication channel  136 , through bridge-tied load  144 , through communication channel  124 , and to ground in pull-down network  122 . 
     Note that voltage-mode drivers have a drive-level which is approximately a linear function of the source resistance. Therefore, once the source resistance of the voltage-mode driver is set to match the impedance of the communication channel, the drive-level of the voltage-mode driver is fixed. In order to get a stronger drive-strength, the resistance of the voltage-mode driver must be reduced. Unfortunately, by reducing the resistance of the voltage-mode driver, the impedance of the driver is no longer matched with the impedance of the communication channel, which can cause noise problems on the communication channel. Note that noise results when the impedance mismatch causes electrical energy to reflect back and forth through the network. 
     Current-Mode Drivers 
       FIG. 2A  presents a block diagram of a current-mode driver. It contains pull-up network  202 , pull-down network  204 , communication channel  206 , switches  208 ,  210 ,  214 , and  216 , current source  212 , current sink  218 , control signal  220 , and termination  222  and  224 . 
     When the current-mode transmits a high bit, control signal  220  closes switches  210  and  214  and leaves switches  208  and  216  open. This causes current to flow from the power supply in pull-up network  202  into communication channel  206 . Note that closing switch  214  provides a current path from the power supply to ground through pull-down network  204 . 
     When the current-mirror-logic driver transmits a low bit, control signal  220  closes switches  208  and  216  and leaves switches  210  and  214  open. This causes current to flow from communication channel  206  to ground through pull-down network  204 . Note that closing switch  208  provides a current path from the power supply to ground through pull-up network  202 . 
     Note that this current-mode driver has a source resistance that matches the line impedance of the communication channel. The current source is a Norton-equivalent current source, which has a source resistance in parallel with the current source (not shown in  FIG. 2 ). Furthermore, this source resistance is set independently of the drive-level. Hence, the drive-level of the current-mode driver can be adjusted without affecting the impedance of the current-mode driver. 
     Note that the act of closing switch  208  by itself dumps current from current source  212  to ground, which causes the circuit to consume power. 
     Also note that pull-up network  202  and pull-down network  204  can be implemented in any semiconductor technology, including: CMOS, biCMOS, GaAs, etc. In a standard CMOS process, the current source in the pull-up network includes a current mirror circuit that mirrors a current from a reference current source. Similarly, current sink in the pull-down network also includes a current mirror circuit that mirrors a current from a reference current sink. Note that these current sources and current sinks consume power at all times. 
       FIG. 2B  presents a block diagram of current-mode drivers configured for differential-mode operation. It contains current source  224 , communication channels  226  and  228 , bridge-tied load  230 , switches  232 ,  234 ,  236 ,  238 , and  240 , control signal  242 , and terminations  242  and  244 . 
     When transmitting a high bit, control signal  242  closes switches  234  and  236  and leaves switches  232 ,  238 , and  240  open. This causes current to flow from current source  224 , through communication channel  226 , through bridge-tied load  230 , through communication channel  228 , and to ground. 
     When transmitting a low bit, control signal  242  closes switches  238  and  240  and leaves switches  232 ,  234 , and  236  open. This causes current to flow from current source  224 , through communication channel  228 , through bridge-tied load  230 , through communication channel  226 , and to ground. 
     Note that the system can alternatively be configured so that the current flows in the opposite direction. For instance, when transmitting a high bit, control signal  242  can close switches  238  and  240  and leave switches  232 ,  234 , and  236  open. This causes current to flow from current source  224 , through communication channel  228 , through bridge-tied load  230 , through communication channel  226 , and to ground. 
     Note that since current is always flowing in the current-mode driver, it consumes more power than the voltage-mode driver. 
     Also note that closing switch  232  by itself dumps current from current source  224  to ground, which causes the circuit to consume power. 
     Coupled Voltage-Mode and Current-Mode Drivers 
       FIG. 3A  illustrates an idealized voltage-versus-time plot of a signal after transmission through a lossy communication channel. This plot illustrates a differential signaling scheme wherein the driver transmits three high bits, a low bit, and then a high bit. It contains rising edges  302 ,  312 , and  314 , falling edges  304 ,  310 , and  316 , and steady states  306  and  308 . The curve initially going high is the “plus” differential line and the curve initially going low is the “minus” differential line. 
     When transmitting a high signal, the driver causes rising edge  302  in the “plus” differential line and falling edge  304  in the “minus” differential line. Since the driver needs to transmit two more high bits, the driver holds the signal steady (steady states  306  and  308 ) until the next transition. The driver then causes falling edge  310  in the “plus” differential line and rising edge  312  in the “minus” differential line to transmit a low bit. After transmitting the low bit, the “plus” differential line returns high (rising edge  314 ) and the “minus” differential line returns low (falling edge  316 ) to transmit a high bit. 
     Note that the voltage level for the “plus” differential line never crosses the voltage level for the “minus” differential line after the driver transmits a low bit because the frequency dependent losses in the communication channel attenuates the high-frequency components of the rising and falling edge signals so that the full voltage range is not reached prior to the next transition. Hence, in this case, the differential lines do not have the correct voltages for the bits transmitted. Also note that the communication channel does not attenuate steady state signals. 
     Furthermore, note that the transition from a high state to a low state occurs over several bit times. In  FIG. 3A , each bit time is denoted by the vertical dashed-line. 
     In one embodiment of the present invention, in order to boost the drive-strength of the voltage-mode driver, a current source is coupled to the voltage-mode driver. The resistance of the voltage-mode driver is set such that it matches the impedance of the communication channel. As mentioned previously, the current source can boost the signal without affecting the impedance of the driver. In order to compensate for the frequency dependent losses, during a signal transition, the current source boosts the drive-strength of the voltage-mode driver. After the signal transitions, the system turns off the current source and returns the drive-level to a lower value by only maintaining power to the voltage-mode driver. 
       FIG. 3B  illustrates an idealized voltage-versus-time plot of a signal after transmission through a lossy communication channel using a current source to boost the drive-level of the voltage-mode driver. This plot illustrates a differential signaling scheme wherein the driver transmits three high bits, a low bit, and then a high bit. It contains rising edges  318 ,  328 , and  332 , falling edges  320 ,  326 , and  330 , and steady states  322  and  324 . The curve initially going high is the “plus” differential line and the curve initially going low is the “minus” differential line. 
     Note that after causing rising edge  318  in the “plus” differential line and falling edge  320  in the “minus” differential line to transmit a high bit, the driver holds the signal steady to transmit the other two high bits (steady states  322  and  324 ). Note that the voltage levels of steady states  322  and  324  are lower than the voltage levels at steady states  306  and  308  in  FIG. 3A . By doing so, when the driver transmits a low bit by causing falling edge  326  in the “plus” differential line and rising edge  328  in the “minus” differential line, the “plus” differential line crosses the voltage level of the “minus” differential line even though the driver subsequently transmits a high bit (rising edge  332  and falling edge  330 ). In this case, the boost-enabled driver compensates for frequency dependent losses and yields the correct voltage levels for the bits transmitted. Also note that the boost-enabled driver makes the signal eye larger and thereby facilitates easier detection of the signal. 
     Also, note that the transition from a high state to a low state occurs over several bit times. In  FIG. 3B , each bit time is denoted by the vertical dashed-line. 
       FIG. 4  presents a block diagram of a current source coupled to a voltage-mode driver in accordance with an embodiment of the present invention. It contains pull-up networks  402  and  412 , pull-down networks  404  and  414 , switches  406 ,  408 ,  418 ,  420 ,  424 ,  428 , control signals  410  and  430 , current source  416 , current sink  422 , communication channel  432 , and termination  434 . 
     Pull-up network  402  and pull-down network  404  form the voltage-mode driver. Pull-up network  412  and pull-down network  414  form the current source. This circuit operates in a similar manner as described in  FIG. 1A  and  FIG. 2A . The only difference is that when transmitting a bit which has a state different from the previously transmitted bit, the system activates the current source to boost the signal. For instance, when transmitting a high bit after transmitting a low bit, control signal  430  closes switches  420  and  424  and leaves switches  418  and  428  open. Current flows from the power source in pull-up network  412 , through communication channel  432  to boost the signal transmitted by the voltage-mode driver. If the driver is transmitting the same bit, or in other words maintaining the same signal state, the current source is not used. 
     In one embodiment of the present invention, the current source and current sink are sized in order to provide sufficient current to boost the voltage-level of the transmitted signal provided by the voltage-mode driver to compensate for frequency dependent losses in the communication channel. In this embodiment, the current source consumes less power than a pure current-mode driver because the current source provides a boost to the drive-strength of the voltage mode driver instead of providing the full drive-strength. 
       FIG. 5  presents a block diagram of a current source coupled to a voltage-mode driver configured for differential-mode operation in accordance with an embodiment of the present invention. It contains pull-up network  502  and  512 , pull-down network  504  and  514 , switches  506 ,  508 ,  516 ,  518 ,  524 ,  526 ,  528 ,  530 ,  532 , control signals  510 ,  520 , and  534 , current source  522 , communication channels  536  and  538 , and bridge-tied load  540 . 
     Both the differential voltage-mode driver and the current source operate in a similar manner as described in  FIG. 1B  and  FIG. 2B . The only difference is that when transmitting a bit which has a state different from the previously transmitted bit, the system activates the current source to boost the signal. For instance, when transmitting a high bit after transmitting a low bit, control signal  534  closes switches  526  and  528  and leaves switches  524 ,  530 , and  532  open. Current flows from current source  522  through communication channel  536 , through bridge-tied load  540 , through communication channel  538 , and to ground. If the driver is transmitting a bit with the same state as a previously transmitted bit, or in other words maintaining the same signal state, the current source is not used. 
     In one embodiment of the present invention, the activation of the current source does not occur at the same time as the activation of the voltage-mode driver, thereby facilitating the optimization of the shape of the transmitted signal in addition to boosting the drive-level of the transmitted signal. In one embodiment of the present invention, multiple current sources are used to optimize the shape of the transmitted signal after traversing a channel with frequency dependent losses. 
     Transmitted Signal Shaving 
       FIG. 6  presents a block diagram of multiple current sources used to optimize the shape of the transmitted signal in accordance with an embodiment of the present invention. It contains input  600 , flip-flops  602 ,  604 , and  606 , decoder  608 , current sources  610 ,  612 ,  614 , and  616 , and output  618 . The current sources boost the signal strength generated by the voltage-mode driver by injecting current through output  618 , which is coupled to the communication channel. 
     During operation, a bit stream enters at input  600 . The system compares the given bit at input  600  to the previously transmitted bit in flip-flop  602 . Decoder  608  determines if the previously transmitted bit and the given bit have the same state. If the previously transmitted bit and the given bit have different states, decoder  608  activates the current sources to optimize the shape and to boost the drive-level of the transmitted signal. In one embodiment of the present invention, decoder  608  activates only one of the current sources. For instance, decoder  608  activates current source  610 . In one embodiment of the present invention, decoder  608  activates more than one of the current sources to boost the signal sent by the voltage-mode driver. For instance, decoder  608  activates current sources  612  and  616 . 
     In one embodiment of the present invention, the system looks at more than just the previously transmitted bit in order to boost the signal sent by the voltage-mode driver. For instance, when comparing the history of the transmitted bits to the given bit at input  600 , the system looks at the previously transmitted bit stored in flip-flop  602  as well as the bit transmitted prior to the previously transmitted bit, which is stored in flip-flop  604 . Decoder  608  then activates the current sources to optimize the shape and boost the drive-level of the transmitted signal. For instance, if the given bit is low, the previously transmitted bit was high, and bit prior to the previously transmitted bit was high, decoder  608  activates current sources  610 ,  612 , and  614 . However, if the given bit is low, the previously transmitted bit is high, and the bit prior to the previously transmitted bit is low, decoder  608  only activates current sources  614 . 
     In one embodiment of the present invention, the current sources have different drive strengths in order to facilitate the optimization of the shape and to boost the drive-level of the transmitted signal. In one embodiment of the present invention, the activation of the current sources does not occur at the same time as the activation of the voltage-mode driver. If more than one current source is coupled to the voltage-mode driver, the system can activate each current-mode-driver separately from the other drivers, thereby facilitating the optimization of the shape and to boost the drive-level of the transmitted signal. 
     In one embodiment of the present invention, decoder  608  is a look-up-table. 
     Boosting Signal Strength 
       FIG. 7  presents a flow chart illustrating process of activating the current source to boost the drive-level of the voltage-mode driver in accordance with an embodiment of the present invention. The process begins when the system reads the state of the given bit to be transmitted (step  702 ). The system then reads the state of the previously transmitted bit (step  704 ). Next, the system determines if the given bit has the same state as the previously transmitted bit (step  706 ). If so, the system does not activate the current source. Otherwise, the system activates the current source to boost the signal of the transmitted bit (step  708 ). 
     Note that this process can be enhanced to optimize the shape of the transmitted signal by using multiple previously transmitted bits. Instead of reading the previously transmitted bit in step  704 , the system reads the history of previously transmitted bits. Next, the system compares the history of previously transmitted bits to the given bit and determines which current sources to activate, replacing step  706 . 
     The foregoing descriptions of embodiments of the present invention have been presented only for purposes of illustration and description. They are not intended to be exhaustive or to limit the present invention to the forms disclosed. Accordingly, many modifications and variations will be apparent to practitioners skilled in the art. Additionally, the above disclosure is not intended to limit the present invention. The scope of the present invention is defined by the appended claims.

Technology Category: 5