Patent Document

CROSS-REFERENCE TO RELATED APPLICATIONS 
     This application is related to U.S. patent application Ser. No. 09/409,923 entitled PARITY-SENSITIVE VITERBI DETECTOR AND METHOD FOR RECOVERING INFORMATION FROM A READ SIGNAL, Ser. No. 09/410,274, and U.S. patent application entitled CIRCUIT AND METHOD FOR RECOVERING SYNCHRONIZATION INFORMATION FROM A SIGNAL, which have the same filing date as the present application and which are incorporated by reference. 
    
    
     TECHNICAL FIELD 
     The invention relates generally to signal encoding and more particularly to a technique for encoding data for storage on a magnetic medium such as a computer disk. 
     BACKGROUND OF THE INVENTION 
     The operating speeds of peripheral computer components such as disk drives often prevent computer engineers from designing faster computer systems. The speeds of microprocessors, which are at the hearts of today&#39;s computer systems, have increased dramatically within the last few years. But the speeds of today&#39;s disk drives and semiconductor memory circuits have lagged behind. Therefore, these slower peripheral components typically limit the overall speed of a computer system because the system microprocessor must effectively “slow down” to transfer data to and from these components. That is, these slower components are the “weak link in the chain”. Fortunately, the new RAMBUS® architecture promises to make the next generation of semiconductor memory circuits as fast or faster than the next generation of microprocessors. But, there have been no speed-increasing breakthroughs of this magnitude in disk-drive technology. 
     Unfortunately, conventional data-encoding techniques can further reduce the already slow data-transfer rates of many disk drives. For example, many data codes are relatively inefficient, i.e., use a relatively large number of code bits per data bit, and thus may significantly reduce the effective writing speed of a disk drive. Furthermore, many data codes are poorly designed, and thus may significantly reduce the effective reading speed of a disk drive. Specifically, if the system processor initially detects a read error, then it tries to correct the error using conventional error-correction techniques. If the processor cannot correct the error using these techniques, then it instructs the disk drive to re-read the data. Unfortunately, error detection, error correction, and data re-read are time-consuming actions that can significantly reduce the effective reading speed of a disk drive. 
     FIG. 1 is a block diagram of a conventional disk-drive write channel  10 , which includes an encoder  12  for encoding data into a Non-Return-To-Zero-Interleave (NRZI) sequence of conventional Run-Length-Limited (RLL) code words. The write channel  10  also includes a pre-coder  14  for converting this NRZI sequence of code words into a corresponding Non-Return-To-Zero (NRZ) sequence of code words. A write-head driver circuit  16  provides the NRZ sequence of code words to a write head  18 , which writes the code words onto a magnetic storage medium  20  such as a hard disk. 
     Unfortunately, conventional RLL coding techniques often limit the speed at which the channel  10  can write data to the medium  20 , and thus limit the data-write speed of the disk drive containing the channel  10  and the medium  20 . As discussed below in conjunction with FIGS. 3 and 4, an RLL code word is often relatively inefficient, and this inefficiency limits the effective speed at which the channel  10  can write data to the medium  20 . Therefore, it is difficult if not impossible to realize significant increases in data-write speeds using conventional RLL coding techniques. 
     FIG. 2 is a block diagram of a conventional read channel  22 , which reads the NRZ sequence of RLL code words that the write channel  10  (FIG. 1) wrote to the storage medium  20 . The read channel  22  includes a read head  24  for reading the code words stored on the medium  20  and for generating a corresponding read signal. A read circuit  26  amplifies the read signal, and a Viterbi detector  28  recovers the NRZ sequence of RLL code words from the read signal. A post-coder  30  converts the recovered NRZ sequence into the corresponding NRZI sequence, and a decoder  32  decodes the NRZI sequence into the read data. Assuming there are no read errors, the recovered NRZ sequence, NRZI sequence, and read data are respectively the same as the NRZ sequence generated by the pre-coder  14 , the NRZI sequence generated by the encoder  12 , and the write data provided to the encoder  12  (FIG.  1 ). Therefore, the read channel  22  is effectively the inverse of the write channel  10 . 
     Unfortunately, conventional RLL coding techniques often limit the speed at which the channel  22  can read data from the medium  20 , and thus limit the data-read speed of the disk drive containing the channel  22  and the medium  20 . As discussed above in conjunction with FIG. 1, an RLL code word is relatively inefficient, and this inefficiency limits the effective speed at which the channel  22  can read data from the medium  20 . Furthermore, as discussed below in conjunction with FIGS. 3 and 4, an RLL code word may significantly degrade the signal-to-noise ratio (SNR) of the data-read signal. Unfortunately, this inefficiency and the degraded SNR limit the effective speed at which the channel  22  can read data from the medium  20 . Therefore, it is difficult if not impossible to realize significant increases in data-read speed using conventional RLL coding techniques. 
     In conjunction with FIGS. 3-10, a general discussion of conventional data read/write and encoding techniques is included to assist the reader in understanding the subsequently discussed inventive concepts. Numerous detailed discussions of these conventional techniques are included in available references such as “Digital Baseband Transmission” by Jan W. Bergmans. 
     Referring to FIGS. 3 and 4, conventional RLL encoding techniques and code words are discussed. Generally, RLL code words are stored on a computer disk instead of data words because the code words can be selected to have desirable parameters that the data words will not always have. As discussed below, the read channel  22  (FIG. 2) depends on these parameters for proper operation. 
     FIG. 3 is a data word  40  and its equivalent RLL code word  42 . The word  40  includes data bits D 0 -D a , and the code word  42  includes code bits C 0 -C b  and is compatible with an x/y RLL (d/k) code. The parameter x/y is the efficiency of the RLL code, and indicates that the code word  42  encodes x=a+1 data bits with y=b+1 code bits. Therefore, the higher the ratio x/y, the fewer the number of code bits that are written and read for each data bit, and thus the faster the data-write and data-read speeds for a given number of data bits. Conversely, the lower the ratio x/y, the greater the number of code bits that are written and read for each data bit, and thus the slower the data-write and data-read speeds for a given number of data bits. The parameter d is the minimum number of code bits C required between consecutive code-bit transitions, and the parameter k is the maximum number of code bits C allowed between consecutive code-bit transitions. For example, binary code sequences 01 and 10 include 0-to-1 and 1-to-0 code-bit transitions, respectively, and an x/y RLL (0/7) code may include the binary sequence 101000000001, which respectively includes 0 bits (minimum) and 7 bits (maximum) between consecutive code-bit transitions. The Viterbi detector  28  (FIG. 1) includes a state machine having a structure based on the responses of the portion of the read channel  22  that includes the read head  24  and read circuit  26 , and possibly on the state sequence of the code if such a state sequence exists. Furthermore, the detector  28  or a separate clock detector (not shown) uses the code-bit transitions to synchronize a read clock signal for sampling the read signal from the read head  24 . 
     FIG. 4 shows the first three code words  42   a,    42   b,  and  42   c  of a code sequence  44 , which is compatible with an 8/9 RLL (0/7) code. Because d=0, there need be no code bits between code-bit transitions. That is, the sequence  44  can have consecutive code-bit transitions such as in the binary series 010101. To insure that the sequence  44  never has more than k=7 code bits between consecutive code-bit transitions, each code word  42   a - 42   c  is selected to have at least one respective transition within one or more predefined code-word sections. For example, having at least one transition in both of the code-word sections  46   a - 46   c  (C 0 -C 3 ) and  48   a - 48   c  (C 6 -C 8 ) of each respective code word  42   a - 42   c  guarantees that the sequence  44  never has more than 7 bits between consecutive code-bit transitions. 
     Unfortunately, because they are typically designed to have relatively small error propagations, RLL codes are often relatively inefficient. As discussed above, such inefficiency reduces the data-transfer speeds of the write and read channels  10  and  22  (FIGS. 1 and 2 ). For example, an 8/9 RLL code word represents 8 bits (a byte) of data. If there is an error in the 9-bit code word, then there is a read error in at most one byte of data. If there is an error that crosses the boundary between two consecutive 8/9 code words, then there is a read error in at most two bytes of data. Thus, the error propagation of the 8/9 RLL code is somewhere between 1 and 2 bytes. On the other hand, because a 16/17 code word represents 2 bytes of data, a code-word error can cause read errors in up to 2 bytes of data, and a cross-boundary error can cause read errors in up to 4 bytes of data. Thus, the error propagation of the 16/17 RLL code is approximately twice that of the 8/9 RLL code. Therefore, even though an RLL code having short code words is typically more inefficient than an RLL code having longer code words, the short-word RLL code is often preferred because it has a smaller error propagation. 
     Furthermore, because RLL codes are typically designed to reduce the occurrence of a specific type of read error, RLL code sequences often have relatively large numbers of bit transitions. This relatively high rate of bit transitions typically lowers the SNR of the read signal, and thus typically reduces the accuracy and effective speed of the read channel  22  (FIG.  2 ). For example, a Maximum-Transition-Rate (MTR) code is a popular RLL code that is designed to eliminate or reduce the occurrence of tri-bit read errors, which are three consecutive erroneous code bits. Tri-bit errors typically occur in three-bit sequences that have two bit transitions, such as 101 being erroneously read as 010. Therefore, MTR codes are typically structured to avoid long sequences of consecutive code-bit transitions. Unfortunately, MTR codes can do very little to increase accuracy if a significant number of the errors are not tri-bit errors. 
     Referring to FIGS. 5-8, NRZI and NRZ sequences are discussed. As discussed below, the combination of the NRZI-to-NRZ conversion in the write channel  10  (FIG. 1) and the NRZ-to-NRZI conversion in the read channel  22  (FIG. 2) prevents reverse connection of the write head  18  or the read head  24  from causing data errors. Typically, the write head  18  and the read head  24  each have two connection terminals. The polarities of the heads  18  and  24  depend on how these terminals are connected to the write circuit  16  and the read circuit  26 , respectively. For example, if connected to have a positive polarity, the write head  18  does not invert the code bits from the circuit  16 , and thus writes a logic 0 from the circuit  16  as a logic 0 and writes a logic 1 from the circuit  16  as a logic 1. Conversely, if connected to have a negative polarity, the write head  18  inverts the code bits from the circuit  16 , and thus writes a logic 0 from the circuit  16  as a logic 1 and writes a logic 1 from the circuit  16  as a logic 0. A similar analysis can be made for the read head  24 . Therefore, if both the write and read heads  18  and  24  are connected to have the same polarity (either positive or negative), then the read data generated by the read channel  22  has the same polarity as the write data input to the write channel  10 . But if the write and read heads  18  and  24  are connected to have different polarities, then the read data has the opposite polarity from the write data, and thus a catastrophic read error occurs. Unfortunately, today&#39;s manufacturing techniques make such reverse-polarity head connections relatively common. Therefore, as discussed below in conjunction with FIGS. 7 and 8, a NRZI-NRZ-NRZI conversion is used because it cancels out such head-polarity errors. 
     FIG. 5 is a schematic diagram of the pre-coder  14  (FIG.  1 ), which converts a NRZI sequence into a NRZ sequence. The pre-coder  14  includes an XOR gate  50 , which receives the NRZI sequence of bits on an input terminal  52  and provides a corresponding NRZ sequence of bits on an output terminal  54 . The pre-coder  14  also includes a first-order delay  56  connected between an input terminal  58  and the output terminal  54  of the XOR gate  50 . Therefore: 
     
       
           NRZout   T   =NRZlin   T   ⊕NRZout   T−1   (1) 
       
     
     where ⊕ is the mathematical symbol for the XOR operation and T represents a discrete point in time. 
     In operation, any sequence of bits—such as the sequence from the encoder  12  (FIG.  1 )—can be arbitrarily labeled as a NRZI sequence, and the pre-coder  14  converts this sequence into a corresponding NRZ sequence of bits. 
     FIG. 6 is a schematic diagram of the post-coder  30  (FIG.  2 ), which converts a NRZ sequence into a NRZI sequence. The post-coder  30  includes an XOR gate  60 , which receives the NRZ sequence of bits on an input terminal  62  and provides the corresponding NRZI sequence of bits on an output terminal  64 . The post-coder  30  also includes a first-order delay  66  connected between the input terminal  62  and another input terminal  68 . Therefore: 
     
       
           NRZIout   T   =NRZin   T   ⊕NRZin   T−1   (2) 
       
     
     In operation, any sequence of bits—such as the sequence from the Viterbi detector  28  (FIG.  2 )—can be arbitrarily labeled as a NRZ sequence, and the post-coder  30  converts this sequence into a corresponding NRZI sequence of bits. As discussed below in conjunction with FIGS. 7 and 8, if the output terminal  54  of the pre-coder  14  (FIG. 5) is coupled to the input terminal  62  of the post-coder  30 , then NRZIin T =NRZIout T . 
     FIG. 7 is an example of a NRZI-NRZ-NRZI conversion using the pre-coder  14  (FIG. 5) and the post-coder  30  (FIG.  6 ). Assume a binary NRZI sequence of 010110 and that NRZT T−1  (the output of the delay  56  at time T−1)=0. First, the pre-coder  14  performs the NRZI-to-NRZ portion of the conversion starting with the first bit (the right-most bit in this example) of the NRZI sequence and ending with the last bit (the left-most bit in this example) of the NRZI sequence. Therefore, the resulting NRZ sequence is 1100100, which includes NRZ T−1  as the first bit. By staggering the NRZ sequence such that its bits are between the bits of the NRZI sequence, one can see that the NRZI sequence is the derivative of the NRZ sequence. That is, wherever NRZI T =1, a transition occurs between the corresponding bits of the NRZ sequence. Conversely, wherever NRZI T =0, no transition occurs between the corresponding bits of the NRZ sequence. For example, the second bit (from the right) of the NRZI sequence is logic 1, and the second and third bits of the NRZ sequence are logic 0 and logic 1, respectively. Thus, NRZI T+1 =logic 1 indicates that there is a transition between NRZ T  and NRZ T+1 . Similarly, the fourth bit of the NRZI sequence is logic 0, and the fourth and fifth bits of the NRZ sequence are logic 0. Thus, NRZI T+3 =logic 0 indicates that there is no transition between NRZ T+2  and NRZ T+3 . Next, the post-coder  30  performs the NRZ-to-NRZI portion of the conversion starting with the first (right-most) bit of the NRZ sequence and ending with the last (left-most) bit. Therefore, the resulting NRZI sequence is 010110, which is the same NRZI sequence we started with. 
     FIG. 8 illustrates the ability of the NRZI-NRZ-NRZI conversion to cancel negative head polarities. For example, if either the write head  18  (FIG. 1) or the read head  24  (FIG.  2 )—but not both—is connected to have a negative polarity, then the Viterbi detector  28  (FIG. 2) generates {overscore (NRZ)}. But despite this inversion, the post-coder  30  recovers the original NRZI sequence 010110. 
     Referring to FIG. 9, parity is a technique used to detect errors in uncoded data. For example, before a binary data byte D is transmitted, it is assigned a parity bit P whose value depends on the values of the bits D 0 -D 7 . The combination of D and P forms a 9-bit parity word  72 . For even parity, the value of P is such that the total number of “1&#39;s” in the word  72  is even. Therefore, if the number of “1&#39;s” in D is odd, then P=1. Likewise, if the number of “1&#39;s” in D is even, then P=0. For odd parity, the value of P is such that the total number of “1&#39;s” in the word  72  is odd. Therefore, if the number of “1&#39;s” in D is odd, then P=0. Likewise, if the number of “1&#39;s” in D is even, then P=1. For example, if D=10101010, then there are four “1&#39;s” in D. Therefore, P=0 for even parity and P=1 for odd parity. Similarly, if D=10101011, then there are five “1&#39;s” in D. Therefore, P=1 for even parity and P=0 for odd parity. The word  72  is then transmitted to a decoder (not shown) that checks the parity of the word  72 . If the parity is incorrect, then the decoder identifies the word  72  as including an error. One may then attempt to recover the correct value of D using conventional error-correction techniques. 
     Although parity is widely used for error detection in uncoded data, it is rarely, if ever, used for error detection in RLL coded data. 
     SUMMARY OF THE INVENTION 
     In one aspect of the invention, a code word includes a first group of data bits and includes code bits that represent a second group of data bits. In another aspect of the invention, there is a minimum probability of bit transitions among the code bits. In yet another aspect of the invention, the code word includes a parity bit. 
     Unlike conventional codes, a code that includes such a code word can have both a high efficiency and a small error propagation. Additionally, by including fewer bit transitions, a sequence of such code words causes less read noise, and thus causes fewer read errors as compared to sequences of known code words. Moreover, such a code word can include a parity bit to allow improved error detection as compared to known error-detection techniques for coded data. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is a block diagram of a data write channel and a storage medium according to the prior art. 
     FIG. 2 is a block diagram of a data read channel and a storage medium according to the prior art. 
     FIG. 3 is a diagram of a data word and a corresponding code word according to the prior art. 
     FIG. 4 is a diagram of a RLL code word according to the prior art. 
     FIG. 5 is a schematic diagram of the pre-coder of FIG.  1 . 
     FIG. 6 is a schematic diagram of the post-coder of FIG.  2 . 
     FIG. 7 is a diagram of an example NRZI-NRZ-NRZI conversion performed by the pre-coder of FIG.  5  and the post-coder of FIG.  6 . 
     FIG. 8 is a diagram of an example {overscore (NRZ)}-NRZI conversion performed by the post-coder of FIG.  6 . 
     FIG. 9 is a diagram of a parity word according to the prior art. 
     FIG. 10 is a diagram of a data word and a corresponding code word according to an embodiment of the invention. 
     FIG. 11 is a diagram of a data word and a corresponding parity code word according to an embodiment of the invention. 
     FIG. 12 is a block diagram of a data encoder according to an embodiment of the invention. 
     FIG. 13 is a block diagram of a data decoder according to an embodiment of the invention. 
     FIG. 14 is a block diagram of a disk-drive system that incorporates the data encoder of FIG. 12, the data decoder of FIG. 13, or both. 
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     FIG. 10 is a diagram of a data word  100  and a corresponding RLL code word  102  according to an embodiment of the invention. As discussed below, a sequence of code words  102  is significantly more efficient and contains significantly fewer code-bit transitions than sequences of prior code words. Furthermore, the error propagation of the associated RLL code is relatively small even though the code efficiency is relatively high. Therefore, a write channel can typically write a sequence of such code words more quickly than it can write a sequence of conventional code words, and a read channel can typically read a sequence of such code words more quickly than it can read a sequence of conventional code words. 
     In one embodiment, the data word  100  includes three data bytes  104   a,    104   b,  and  104   c,  and the code word  102  is a 24/25 RLL (0/14) code word that includes a coded portion  106  and an uncoded portion  108 . The coded portion  106  includes a number of code bits C, here seventeen code bits C 0 -C 16 , which represent the data bytes  104   a  and  104   b.  Conversely, the uncoded portion  108  does not include code bits, but instead includes the data bits D C0 -D C7  of the data byte  104   c.  That is, the uncoded portion  108  is identical to the data byte  104   c.  To insure that a sequence of code words  102  never has more than 14 bits between consecutive transitions, the coded portion  106  is selected such that there is at least one transition within each of the following sections of code bits: the first three bits C 0 -C 2 , the middle eleven bits C 3 -C 13 , and the last three bits C 14 -C 16 . In other embodiments, however, the code word  102  can have different x/y and d/k ratings, the coded and uncoded portions  106  and  108  can have different lengths, and the coded portion  106  can have different code-bit transition sections. 
     In addition to having a higher efficiency than a sequence of conventional code words, a sequence of code words  102  also has a lower error propagation with respect to its efficiency than a sequence of conventional code words. This lower error propagation is due to the code word  102  having two portions instead of only one portion. For example, an error in the uncoded portion  108  causes a data error in at most one data byte  104   c.  Likewise, an error in the coded portion  106  causes a data error in at most two data bytes  104   a  and  104   b.  Furthermore, because the coded portions  106  are separated by the uncoded portions  108  in a sequence of code words  102 , a cross-boundary error causes a data error in at most three data bytes  104   a,    104   b,  and  104   c.  Therefore, compared to a sequence of conventional code words such as the 16/17 code word discussed in conjunction with FIG. 4, a sequence of the code words  102  has a significantly higher efficiency (24/25 versus 16/17 ) and a significantly lower error propagation (between 1 and 3 bytes versus between 2 and 4 bytes). Furthermore, as discussed below, the code words  102  can be constructed so that a sequence of code words  102  has an even lower error propagation. 
     Still referring to FIG. 10, in another embodiment of the invention, the code word  102  is designed according to a Minimal Transition Probability (MTP) RLL coding scheme in which the coded portion  106  is selected to have the fewest possible transitions in the form—typically the NRZ form—in which it will be stored. This increases the SNR of the read signal, and thus improves the initial reading accuracy, and thus the effective read speed, of a read channel that reads a sequence of code words  102 . Specifically, it has been found that contrary to the prior-art teachings, a combination of single-bit and tri-bit errors compose approximately 99% of all initial read errors, with single-bit errors composing approximately 80% of all initial read errors and with tri-bit errors composing merely 19% of all initial read errors. Therefore, to provide the greatest overall reduction in total initial read errors, it is clear that a code should be designed to cause as few single-bit errors as possible. It has also been found that a major cause of single-bit errors is bit transitions in the sequence of code words being read. That is, the more transitions the more single-bit errors, and the fewer transitions the fewer single-bit errors. Therefore, it follows that all else being equal, sequences of code words having the fewest code-bit transitions cause the fewest read errors on average. In accordance with these findings, the inventors developed the MTP RLL coding scheme. 
     For example purposes, the development process for a 24/25 MTP RLL (0/14) code having code words  102  is discussed, it being understood that similar processes can be used to develop other MTP RLL codes. 
     First, the code designer selects the coded portions  106  having the fewest possible transitions. Because they include 17 code bits, there are 2 17  possible coded portions  106 . But because these portions  106  represent respective pairs of data bytes  104   a  and  104   b  (16 data bits total), only half (2 16 ) of the possible portions  106  are used. Therefore, the designer first discards all the code portions  106  that do not have at least one transition in each of the following transition sections: C 0 -C 2 , C 3 -C 13 , and C 14 -C 16 . Because they will be converted from the NRZI to the NRZ domain for storage, the code portions  106  are selected such that they have this transition pattern in the NRZ domain. As stated above in conjunction with FIG. 8, a “1” in an NRZI sequence indicates a transition in a corresponding NRZ sequence. Therefore, by discarding the code words that don&#39;t have at least one “1” in each of the transition sections, the designer discards the coded portions  106  that do not meet the given transition requirement in the NRZ domain. From the remaining coded portions  106 , the designer selects the 2 16  that have the fewest bit transitions in the NRZ domain. Again, he does this by selecting the 2 16  coded portions  106  having the fewest “1&#39;s”. 
     Next, the designer assigns the selected coded portions  106  to corresponding 16-bit (two byte) data words in such a way that the 24/25 MTP RLL (0/14) code has a reduced error propagation. Specifically, the designer assigns a coded portion  106  to a data word such that an error in one section of the coded portion  106  causes an error in only one of the corresponding data bytes  104   a  and  104   b.  For example, consider the following assignments in Table A. 
     
       
         
               
               
               
             
           
               
                   
                 TABLE A 
               
               
                   
                   
               
               
                   
                 17-bit Coded Portion 
                 16-bit Data Word 
               
               
                   
                   
               
             
             
               
                   
                 10000000000100001 
                 1111111100000000 
               
               
                   
                 01000000000100001 
                 1001001100000000 
               
               
                   
                   
               
             
          
         
       
     
     Suppose that only coded portions  106  ending in 00100001 (last 8 bits) are assigned to data words ending in 00000000. That is, the decoder (not shown in FIG. 10) “knows” that any coded portion ending in 00100001 represents a data word having a data byte  104   a  equal to 00000000. Therefore, an error in the most significant 9 bits of these coded portions  106  would cause an error in at most one data byte, i.e., the most significant byte  104   b  of the data word. This reduces the error propagation of a series of such code words  102  because not all errors in the coded portions  106  will cause errors in two data bytes. 
     Appendix A lists 2 16  coded portions  106  for a 24/25 MTP RLL (0/14) code developed according to an embodiment of the above-described process. The coded portions  106  are in hexadecimal form, and are in row order with respect to the 16-bit data words that they represent. For example, data word 0000000000000000 is represented by the coded portion  15 B 49 , which is in the upper left-hand corner of page 1 of Appendix A. Likewise, the data word 0000000000000001 is represented by the coded portion  04103 , and so on. 
     Furthermore, because the uncoded portions  108  are identical to the data bytes  104   c,  the portions  108  are not preselected. 
     FIG. 11 is a diagram of the data word  100  and a corresponding RLL parity code word  110 , which includes a parity bit P according to an embodiment of the invention. In one embodiment, the code word  110  includes the code word  102  (FIG. 10) and a parity bit P, and is thus compatible with a 24/26 MTP RLL (0/14) code. Therefore, in addition to the advantages discussed above for a sequence of the code words  102 , a sequence of the parity code words  110  provides the error-detecting advantages discussed above in conjunction with FIG.  9 . 
     The parity bit P is calculated in either the NRZ or NRZI domain to provide the proper parity with respect to the code word  110  in the NRZ domain. This allows a Viterbi detector to check for read errors by checking the parity of the code word  110 . 
     To calculate the parity bit P in the NRZ domain, one first converts the coded and uncoded portions  106  and  108 —which are initially in the NRZI domain—into the NRZ domain. The parity-bit calculation is then the same as that discussed above in conjunction with FIG.  5 . 
     To calculate the parity bit P in the NRZI domain, one must take into account how the NRZI-to-NRZ conversion will affect the values of P and the other bits of the code word  110 . According to one technique for generating the code word  110  having even parity, P in the NRZI domain (P evenNRZI ) equals the sum of every other bit of the code word  102  (i.e., every other bit of the code word  110  other than P) starting with C 1 . Thus, where the code word  102  is 25 bits long, P evenNRZI  is given by the following equation: 
     
       
           P   evenNRZI   =C   1   ⊕C   3   ⊕C   5   ⊕C   7   ⊕C   9   ⊕C   11   ⊕C   13   ⊕C   15   ⊕D   C0   ⊕D   C2   ⊕D   C4   ⊕D   C6   (3) 
       
     
     For example, if the code word  102  is 1001110001110011110000110, then P evenNRZI =1⊕0⊕0⊕1⊕1⊕0⊕1⊕1⊕0⊕1⊕1⊕0=1. Therefore, the code word  110  equals 11001110001110011110000110 in the NRZI domain. Using the pre-coder  14  (FIG. 5) and assuming that NRZout T−1 =0, the code word  110  equals 01000101111010001010000010 in the NRZ domain. There are ten “ 1&#39;s ” in the first 25 bits (i.e., all the bits except the parity bit P), and P evenNRZ =0 to provide even parity in the NRZ domain as desired. 
     This parity-calculation technique is derived as follows, where X represents the bits of the code word  110  in the NRZI domain, Y represents the bits of the code word  110  in the NRZ domain, S=NRZout T−1 , and B equals the number of bits Y in the code word  110 . 
     
       
           {Y   0   , Y   1   , . . . , Y   B−1   }={S⊕X   0   , S⊕X   0   ⊕X   1   , . . . , S⊕X   0   ⊕X   1   ⊕ . . . ⊕X   B−1 }  (4) 
       
     
      Parity= Y   0   ⊕Y   1   ⊕ . . . ⊕Y   B−1   (5) 
     Therefore, substituting the NRZI (X) values for the NRZ (Y) values we get: 
     
       
         Parity=[ B⊕S]⊕[B⊕X   0 ]⊕[( B− 1)⊕ X   1 ]⊕ . . . ⊕[2⊕ X   B−2   ]⊕X   B−1   (6) 
       
     
     where ⊕ represents mod2 multiplication such that q⊕r=0 if q is an even number and q⊕r=r if q is an odd number. If q={B, B−1, . . . , 1} and B is an even number, then it follows that:              Parity   =              ∑     n   =   1       B   /   2            X       2      n     -   1              mod2             (   7   )                                
     Because the parity bit is the last element of the right-hand side of equation (7), P evenNRZI  equals the logical sum of all the other elements. So for even parity:                P   evenNRZI     =              ∑     n   =   1         B   /   2     -   1            X       2      n     -   1              mod2             (   8   )                                
     A similar formula can be derived for odd parity. 
     FIG. 12 is a block diagram of a data encoder  120  according to an embodiment of the invention. For example, the encoder  120  can replace the encoder  12  in the write channel  10  of FIG.  1 . Referring to FIGS. 11 and 12, the encoder  120  includes a coded-portion encoder  122 , which receives the data bytes  104   a  (D a0 -D a7 ) and  104   b  (D b0 -D b7 ) in parallel and converts them into the coded portion  106  (C 0 -C 16 ) of the code word  110 . A parity-bit generator  124  receives the uncoded portion  108  (D c0 -D c7 ) and the coded portion  106  in parallel and generates the parity bit P therefrom. In one embodiment, the generator  124  calculates P for even parity using the technique described above in conjunction with FIG.  11 . The encoder  120  also includes a conventional parallel-to-serial converter  126 , which receives the code word  110  in parallel and converts it into a 1-bit wide NRZI bit stream. In one embodiment, this bit stream is processed by a pre-coder such as the pre-coder  14  of FIG.  5 . Furthermore, the encoder  120  can be modified to generate only the code word  102  (i.e., the code word  110  without the parity bit P) by omitting or deactivating the generator  124 . 
     FIG. 13 is a block diagram of a data decoder  130  according to an embodiment of the invention. For example, the decoder  130  can replace the decoder  132  in the read channel  22  of FIG.  2 . Referring to FIGS. 11 and 12, the decoder  130  includes a conventional serial-to-parallel converter  132 , which receives the NRZI bit stream from a post-coder such as the post-coder  30  (FIG. 2) and which converts the bit stream into the code word  110 . A coded-portion decoder  134  receives the coded portion  106  (C 0 -C 16 ) of the code word  110  from the converter  132  and decodes it into the data bytes  104   a  (D a0 -D a7 ) and  104   b  (D b0 -D b7 ). Therefore, assuming there are no write or read errors, the decoder  130  provides the originally encoded bytes data  104   a,    104   b,  and  104   c  (D c0 -D c7 ) at its output. In one embodiment, the parity bit P is analyzed only by a parity-checking Viterbi detector, an embodiment of which is disclosed in U.S. patent application Ser. No. 09/409,923 PARITY-SENSITIVE VITERBI DETECTOR AND METHOD FOR RECOVERING INFORMATION FROM A READ SIGNAL, Therefore, in such an embodiment, the converter  132  may strip P from the code word  110 . 
     FIG. 14 is a block diagram of a disk-drive system  140  according to an embodiment of the invention. Specifically, the disk-drive system  140  includes a disk drive  142 , which incorporates the encoder  120  or the decoder  130  of FIGS. 12 and 13, respectively. The disk drive  142  includes a combination write/read head  144 , a write-channel circuit  146  for generating and driving the head  144  with a write signal, and a write controller  148  for interfacing the write data to the write-channel circuit  146 . In one embodiment, the write-channel circuit  146  is similar to the write channel  10  of FIG. 1 except that the write head  18  is omitted and the encoder  12  is replaced with the encoder  120 . The disk drive  142  also includes a read-channel circuit  152  for receiving a read signal from the head  144  and for recovering the written data from the read signal, and includes a read controller  154  for organizing the read data. In one embodiment, the read-channel circuit  152  is similar to the read channel  22  of FIG. 2 except that the read head  24  is omitted, the decoder  32  is replaced with the decoder  130 , and the Viterbi detector  28  is replaced with the parity-checking Viterbi detector of U.S. patent application Ser. No. 09/409,923 entitled PARITY-SENSITIVE VITERBI DETECTOR AND METHOD FOR RECOVERING INFORMATION FROM A READ SIGNAL. The disk drive  142  further includes a storage medium such as one or more disks  156 , each of which may contain data on one or both sides. The write/read head  144  writes/reads the data stored on the disks  156  and is connected to a movable support arm  158 . A position system  160  provides a control signal to a voice-coil motor (VCM)  162 , which positionally maintains/moves the arm  158  so as to positionally maintain/radially move the head  144  over the desired data on the disks  156 . A spindle motor (SPM)  164  and a SPM control circuit  166  respectively rotate the disks  156  and maintain them at the proper rotational speed. 
     The disk-drive system  140  also includes write and read interface adapters  168  and  170  for respectively interfacing the write and read controllers  148  and  154  to a system bus  172 , which is specific to the system used. Typical system busses include ISA, PCI, S-Bus, Nu-Bus, etc. The system  140  also typically has other devices, such as a random access memory (RAM)  174  and a central processing unit (CPU)  176  coupled to the bus  172 . 
     From the foregoing it will be appreciated that, although specific embodiments of the invention have been described herein for purposes of illustration, various modifications may be made without deviating from the spirit and scope of the invention.

Technology Category: 5