Patent Document

CROSS-REFERENCE TO RELATED APPLICATION  
       [0001]     This application claims the priority benefit of Taiwan application serial no. 92129089, filed on Oct. 21, 2003.  
       BACKGROUND OF THE INVENTION  
       [0002]     1. Field of the Invention  
         [0003]     The present invention is generally related to a voltage level shifter. More particularly, the present invention relates to a voltage level shifter suitable for a driving circuit of a liquid crystal display (LCD), wherein the direct current (DC) path thereof may be broken for preventing the turning on of PMOS transistor and NMOS transistors simultaneously. Therefore, the DC power consumption is reduced, and the layout of the circuit and chip area are also reduced.  
         [0004]     2. Description of the Related Art  
         [0005]     In general, an output stage of a conventional voltage level shifter constructed by metal oxide semiconductors (MOS) includes at least an inverter for buffering. The inverter usually includes a PMOS transistor and a NMOS transistor. The problem generated in the conventional design is that it is hard to control the timing of switching the status between the transistors when the voltage level is changed. It is preferable to minimize the time for turning on both the PMOS transistor and the NMOS transistors during the switching to minimize the power consumption. However, even though the ratio of the channel width to the channel length has been considered carefully and designed, the uncertainty during the manufacturing process will still generate a considerable DC power consumption.  
         [0006]      FIG. 4  is a circuit diagram schematically illustrating a conventional voltage level shifter. Referring to  FIG. 4 , the conventional voltage level shifter includes a differential input for NMOS transistors  411  and  415 . The output stage of the voltage level shifter includes a PMOS transistor  403  and a NMOS transistor  413 , and the output stage is provided for an inverter  431 . The inverter  431  can be, for example, a high voltage inverter. In addition, there is another inverter  433  electrically connected to the transistors  411  and  415 . The inverter  433  usually comprises a low voltage inverter because the driving power of the inverter  433  is less than the inverter  431 . Moreover, the inverter  433  is provided for converting the input clock transistor-transistor logic (TTL) voltage signal VIN to a differential input. Referring to  FIG. 9 , when the input is a clock signal and the clock TTL signal is changed from low to high, the inverter  433  inverts the input signal and outputs a signal to a gate of the transistor  411 , in which the outputted signal is delayed a little after the VIN. Therefore, there is an extremely short period of time that a gate of the PMOS transistor  405  is at analog high voltage low level GNDA when the NMOS transistor  415  is turned on and the NMOS transistor  411  is not turned off. Thus, when the PMOS transistor  405  is still on, the PMOS transistor  405  and the NMOS transistor  415  are turned on at the same time. Thus, as shown in  FIG. 9 , current I( 415 ) has a surge at the beginning of each input cycle. Moreover, for generating the differential input signal pair, the PMOS transistor requires a very fast switching in order that the NMOS transistor can control the gate of the PMOS transistor within a short time. Thus, the ratio of the channel width to the channel length of the transistors is designed to achieve the desired effects described above. Typically, the NMOS transistor is designed to have a smaller impedance, i.e., with channel having a wider width and a shorter length, and the PMOS transistor is designed to have a larger impedance, i.e., with a channel having a narrower width and a longer length.  
         [0007]     Similarly, referring to  FIG. 4  and  FIG. 9 , when the input clock signal is changed from high to low, the NMOS transistor  415  is turned off. At this moment, the gate of the NMOS transistor  411  is not turned on due to a time delay, therefore, the transistor  411  is at a high impedance state. During this time, a gate of the PMOS transistor  401  is at low voltage level, thus the PMOS transistor  401  is still on. Therefore, another conducting path is generated by the PMOS transistor  401  when the NMOS transistor  411  is changed from low to high level, and a current I( 411 ) will generate a surge at this time.  
         [0008]     Thus, the breaking of the conducting path between the high voltage and the ground is required in order to reduce the power consumption during the turning on of both of the PMOS transistor and NMOS transistors to reduce the power consumption of the analog circuit.  
         [0009]     Furthermore, the voltage level shifter that applies to a driving circuit of a LCD occupies significant chip area. The chip area can be more compact if the ratio of the channel width to the channel length is not an issue. Therefore, a voltage level shifter that can reduce the power consumption and the chip area to lower down the cost is required.  
       SUMMARY OF THE INVENTION  
       [0010]     The present invention is to provide a voltage level shifter wherein the current path between the high voltage level and the ground are completely broken.  
         [0011]     Another objective of the present invention is to provide a voltage level shifter wherein the ratio of the channel width to the channel length of the transistors is not a major issue in the circuit design.  
         [0012]     Another objective of the present invention is to provide a voltage level shifter suitable for a driving circuit of a LCD, wherein the chip area is substantially reduced due to the repeating of some circuits.  
         [0013]     The present invention provides at least one voltage level shifter for breaking the current path and for turning on the PMOS transistor and NMOS transistors connected in serial in the circuit at different times. Thus, an input/output control sequence is required. The present invention provides many different input/output timing sequences in the embodiments that can achieve the desired results. This invention may, however, be embodied in many other different forms and should not be construed as limited to the embodiments set forth herein. These embodiments are provided so that this disclosure will be thorough and complete,  
         [0014]     To begin with, an output stage of a voltage level shifter is an inverter. When an input signal of the shifter is at low voltage level, an output signal from the output stage is also at low voltage level. A PMOS transistor should have been turned off before a NMOS transistor is turned on when the input signal is changed from low level to high level. Thus, a control signal is provided with a time period in front of the input signal. The input signal and the control signal are processed by an inverter, thus the PMOS transistor is at a high impedance during the rising of the control signal and the rising of the input signal. During this time, the output stage outputs a low voltage signal and a capacitor stores the original high voltage level of the output stage. The NMOS transistor is turned on when the input signal is changed from low to high level. The NMOS transistor pulls down the voltage stored in the capacitor to low voltage level. At the same time, an inverter pulls up an output terminal to high voltage level.  
         [0015]     Similarly, the NMOS transistor should have been turned off before the PMOS transistor turns on when the input signal changes from high to low level. In other words, the NMOS transistor should also be at high impedance state for another time period before the PMOS transistor is turned on. The capacitor is maintained at the ground level and then the PMOS transistor is turned on, thus a high voltage level is achieved within a short time. During this time, the output stage outputs a low voltage signal. Therefore, the control signal has a direct impact on the operation of the circuit.  
         [0016]     However, the PMOS transistor is turned on when the control signal is periodic and the input signal is at high voltage level. The capacitor is charged up from the ground to high voltage level within a short period of time, and thus an error output is generated. Thus, a switch transistor is connected in between the NMOS transistor and the capacitor for producing another control signal to break the charging path. As a result, the voltage level of the capacitor is maintained. The capacitor keeps to perform the same operation as previously described when the control signal changes back to low voltage level again.  
         [0017]     As a simplified version of the present invention, an AND gate of the input terminal, the PMOS transistor and the NMOS transistor can be three transistors connected in series. The sequence of the connection from high voltage level to the ground includes a first PMOS transistor, a first NMOS transistor and a second NMOS transistor. Wherein, a gate of the second NMOS transistor is electrically connected to the input signal. A gate of the first PMOS transistor and a gate of the first NMOS transistor are electrically connected to a first control signal. Moreover, the transistor in a buffer (for example, an inverter described above) has to be in a proper size in order to drive the next output. Moreover, the capacitor, for example, can be comprised of a second PMOS transistor and a third PMOS transistor connected in series. Wherein, the second PMOS transistor is electrically connected to a high voltage level and a gate of the second PMOS transistor is electrically connected to a second control signal. The third PMOS transistor is electrically connected to the buffer (for example, an inverter), and thus a latch circuit is provided. Furthermore, the switch transistor, for example, can be comprised of a third NMOS transistor. The PMOS transistors can be designed in any size, for example, be high voltage transistors. Thus, the uncertainty generated from the manufacturing process is reduced and the stability of the circuit is enhanced.  
         [0018]     The first control signal produces a negative pulse with very narrow width when the inputted clock signal changes from low to high voltage level. During this time, the second NMOS transistor is turned on and the first control signal changes to low voltage level. As a result, the first and third NMOS transistors are turned off, the first PMOS transistor is turned on and the capacitor keeps the same voltage level. At the same time, the second control signal inputs a positive pulse with a wider pulse width than the pulse width of the first control signal. During this time, the second PMOS transistor is turned off. Thus, a high impedance path is formed between the second and third PMOS transistors. Moreover, the first and third NMOS transistors are turned on and the first PMOS transistor is turned off when the negative pulse from the first control signal ends. At the same time, the capacitor discharges to low voltage level and the output signal changes to high voltage level. The third PMOS transistor turns off due to high voltage level in the output. Although the second PMOS transistor conducts when the positive pulse of the second control signal is off, but because the third PMOS transistor remains in the off state, a high impedance path is formed between the second and third PMOS transistors and the capacitor maintains the low voltage level.  
         [0019]     In the case when the input clock signal is at high voltage level and the first control signal and the second control signal provide a negative pulse and a positive pulse respectively, the first PMOS transistor is turned on. During this time, the first and third NMOS transistors are turned off and the voltage level of the capacitor remains the same as previous.  
         [0020]     Similarly, the first control signal produces a negative pulse with very narrow width when input a clock signal that changes from high to low voltage level. During this time, the second NMOS transistor turns on and the first control signal changes to low voltage level. As a result, the first and third NMOS transistors are turned off, the first PMOS transistor is turned on and the capacitor maintains the same voltage level. Moreover, the first and third NMOS transistors are turned on and the first PMOS transistor is turned off when the negative pulse from the first control signal ends. The second NMOS transistor is turned off because the original input signal is at low voltage level. Hence, the second PMOS transistor temporarily acts as a parasitic capacitor before the positive pulse from the second control signal ends. During this time, the second PMOS transistor is at high impedance state and the output signal is at low voltage level. The second PMOS transistor conducts after the positive pulse from the second control signal ends. Thus, the second and third PMOS transistors form a conducting path. At this time, the capacitor is at high voltage level.  
         [0021]     Similarly, in the case when the input clock signal is at low voltage level and the first control signal and the second control signal provide a negative pulse and a positive pulse respectively, the first PMOS transistor is turned on. During this time, the first and third NMOS transistors are turned off and the voltage level of the capacitor remains the same as previous. Immediately after that, the third PMOS transistor temporarily (with high impedance) acts as a parasitic capacitor for a short period of time (Td).  
         [0022]     Moreover, both of the first and second control signals (for example, high voltage control signals) use positive/negative pulses as the controlling signals to control a voltage level shifter. The first control signal and second control signal provide a negative pulse and a positive pulse respectively when the input status is changed. The width of a negative pulse should be slightly wider than the width of a positive pulse because the time periods between the positive pulse and the negative pulse inevitably results in high impedance. The slightly wider negative pulse also prevents damages resulted from the second and third PMOS transistors being conducted to the first, second and third NMOS transistors when the input signal is at high voltage level.  
         [0023]     Moreover, the first PMOS transistor, the first and third NMOS transistors form conducting paths when the input signal is changed to a high voltage level. Furthermore, the first PMOS transistor and the first NMOS transistor produce smaller surges compared to that of the prior art since the first PMOS transistor/NMOS transistor can be designed in many ways.  
         [0024]     Similarly, the buffer of the output stage (the buffer comprises an inverter made from PMOS transistor/NMOS transistor) also results in a smaller surge (compared to prior art) when the input clock signal is changed from high to low voltage level.  
         [0025]     Accordingly, in the voltage level shifter of the present invention, two control signals are provided to turn on and off the PMOS transistor and NMOS transistors, thus the power consumption during the turning on of the PMOS transistor and NMOS transistors is reduced. Moreover, the current path between the high voltage level and the ground are also broken totally by the two control signals reducing the power consumption of the analog circuit.  
         [0026]     It is to be understood that both the foregoing general description and the following detailed description are exemplary, and are intended to provide further explanation of the invention as claimed. 
     
    
     BRIEF DESCRIPTION OF THE DRAWINGS  
       [0027]     The accompanying drawings are included to provide a further understanding of the invention, and are incorporated in and constitute a part of this specification. The drawings illustrate embodiments of the invention and, together with the description, serve to explain the principles of the invention.  
         [0028]      FIG. 1  is a circuit diagram schematically illustrating a voltage level shifter according to one preferred embodiment of the present invention.  
         [0029]      FIG. 2  is a circuit diagram schematically illustrating a voltage level shifter according to another preferred embodiment of the present invention.  
         [0030]      FIG. 3  is a circuit diagram schematically illustrating a voltage level shifter according to yet another preferred embodiment of the present invention.  
         [0031]      FIG. 4  is a circuit diagram schematically illustrating a conventional voltage level shifter.  
         [0032]      FIG. 5  is a waveform diagram schematically illustrating the simplified input and output voltages of the voltage level shifter of  FIG. 1 .  
         [0033]      FIG. 6  is a waveform diagram schematically illustrating the input and output voltages of the voltage level shifter of  FIG. 1 .  
         [0034]      FIG. 7  is a waveform diagram schematically illustrating the input and output voltages of the voltage level shifter of  FIG. 2 .  
         [0035]      FIG. 8  is a waveform diagram schematically illustrating the input and output voltages of the voltage level shifter of  FIG. 3 .  
         [0036]      FIG. 9  is a waveform diagram schematically illustrating the relationships between the input voltages and currents of the transistors of a conventional voltage level shifter and a voltage level shifter according to one preferred embodiment of the present invention. 
     
    
     DESCRIPTION OF THE PREFERRED EMBODIMENTS  
       [0037]     The present invention now will be described more fully hereinafter with reference to the accompanying drawings, in which preferred embodiments of the invention are shown. This invention may, however, be embodied in many different forms and should not be construed as limited to the embodiments set forth herein; rather, these embodiments are provided so that this disclosure will be thorough and complete, and will fully convey the scope of the invention to those skilled in the art. Like numbers refer to like elements throughout.  
         [0038]      FIG. 1  is a circuit diagram schematically illustrating a voltage level shifter according to one preferred embodiment of the present invention. Referring to  FIG. 1 , an inverter includes, for example but not limited to, a PMOS transistor  101  and a NMOS transistor  111 . The PMOS transistor  101  and the NMOS transistor  111  need to be activated at different times in order to break the current paths.  FIG. 5  is a waveform diagram schematically illustrating the simplified input and output voltages of the voltage level shifter of  FIG. 1 . Referring to  FIG. 5 , the transistor  101  should be turned off before the transistor  111  is turned on when an input VIN (e.g., a clock TTL voltage signal) changes from low to high level. Thus, a control signal VA is input to the voltage level shifter,—in which a timing of the control signal VA is prior to the input VIN by a time period Tdis. The control signal VA, for example, can be a high voltage control signal. The state of VOUT1B prior to the Tdis is at an analog high voltage high level VDDA, and the state of VOUT1B during the period Tdis is at high impedance state. Thus, a capacitor  121  stores the original high level and an output stage of the voltage level shifter outputs an analog high voltage low level GNDA. The transistor  111  is turned on when VIN is at high level, thus the VOUT1B is pulled down to the analog high voltage low level GNDA and the output stage outputs an analog high voltage high level VDDA.  
         [0039]     Similarly, the transistor  111  should be turned off before the transistor  101  is turned on when VIN changes from high to low level. The transistor  111  remains at a high impedance state at a time period Tk before the transistor  101  is turned on. Likewise, the capacitor  121  stores the ground level of VOUT1B. Thus, VOUT1B charges up to VDDA within a short period of time when the transistor  101  is turned on, and the output stage outputs an analog high voltage low level GNDA. Therefore, the control signal VA has a direct impact on the circuit&#39;s operation.  
         [0040]      FIG. 6  is a waveform diagram schematically illustrating the input and output voltages of the voltage level shifter of  FIG. 1 . Referring to  FIG. 1  and  FIG. 6 , the PMOS transistor  101  is turned on when the control signal VA is periodically inputted and the input TTL voltage level (VIN) is at high level. At this moment, VOUT1B is charged up from the analog high voltage low level GNDA to VDDA rapidly, and a wrong output is generated.  
         [0041]      FIG. 2  is a circuit diagram schematically illustrating a voltage level shifter according to another preferred embodiment of the present invention. Referring to  FIG. 2 , a NMOS transistor switch transistor  251  controlled by the control signal is provided for breaking the charging path. As a result, the voltage level of VOUT1B is maintained by the capacitor  221 .  FIG. 7  is a waveform diagram schematically illustrating the input and output voltages of the voltage level shifter of  FIG. 2 . Referring to  FIG. 7 , the voltage level of VOUT2B is maintained by the capacitor  221  when VA is changed to low voltage level.  
         [0042]      FIG. 3  is a circuit diagram schematically illustrating a voltage level shifter according to yet another preferred embodiment of the present invention. In this embodiment of the present invention, only the buffer has to be designed in a proper size (for driving the next output), other MOS transistors can be designed in any sizes for buffering the output and maintaining the signal (as the capacitor  221  shown in  FIG. 2 ). The PMOS transistor can be a field effect transistor (FET) designed in any size, for example, as a high voltage FET, thus the uncertainty in the manufacturing process is reduced and the stability of the circuit is enhanced.  
         [0043]      FIG. 8  is a waveform diagram schematically illustrating the input and output voltages of the voltage level shifter of  FIG. 3 . Referring to  FIG. 3  and  FIG. 8 , the control signal VA produces a delayed negative pulse with very narrow width Twa when a clock TTL voltage signal changes from low to high level. During this period Twa, a NMOS transistor  311  is on, and since VA is pulled down to low level, the NMOS transistor  313  and the switch transistor  351  are turned off rapidly. In addition, the PMOS transistor  301  is turned on and VOUT3B maintains the voltage level. On the other hand, another control signal VB produces a positive pulse with a pulse width of Twb (Twb is wider than Twa) during the time period Twa. During this time period Twb, PMOS transistor  303  is off, therefore a high impedance path is constructed by the PMOS transistors  303  and  305 . The NMOS transistor  313  and the switch transistor  351  are turned on again when the negative pulse of VA is off. Thus, the PMOS transistor  301  is turned off, VOUT3B is pulled down to analog high voltage low level GNDA, and the state of VOUT3 is changed to high voltage high level VDDA. Thus, the PMOS transistor  305  is turned off since VOUT3 is at high voltage high level VDDA. Moreover, the PMOS transistor  303  is turned on since the PMOS transistor  305  is turned off when the positive pulse of VB is off. Similarly, a high impedance path is constructed by the PMOS transistors  303  and  305 , and during this moment, VOUT3B remains at analog high voltage low level GNDA.  
         [0044]     Referring to  FIG. 8 , the PMOS transistor  301  is turned on when the clock TTL voltage signal remains at high level, the control signals VA and VB provide a negative pulse and a positive pulse respectively. During this moment, the PMOS transistor  313  and the switch transistor  351  are turn off and VOUT3B remains at the same voltage level.  
         [0045]     Similarly, the control signal VA produces a delayed negative pulse with very narrow width Twa when a clock TTL voltage signal changes from high to low level. During this moment, the NMOS transistor  313  and the switch transistor  351  are turned off rapidly, the PMOS transistor  301  is turned on and VOUT3B remains at analog high voltage low level GNDA. The NMOS transistor  313  and the switch transistor  351  are turned on when the negative pulse of VA is off. During this time, the PMOS transistor  301  is turned off. In addition, since the VIN is at low voltage level originally so the NMOS transistor  311  is turned off. Therefore, during a time period Td (Td=Twb−Twa), the PMOS transistor  305  is at high impedance state before the positive pulse of VB is off. The PMOS transistor  305  is provided as a junction capacitor (i.e., a parasitic capacitor) as capacitor  221  shown in  FIG. 2 . Thus, VOUT3 is at analog high voltage low level GNDA. The PMOS transistor  303  is turned on rapidly after the positive pulse of VB is off. Thus a conducting path is constructed by the PMOS transistors  303  and  305 , and VOUT3B is at high voltage high level VDDA via the conducting path.  
         [0046]     Moreover, the NMOS transistor  313  and the switch transistor  351  are turned off when a clock TTL voltage signal remains at low level and when the control signals VA and VB provide a negative pulse and a positive pulse respectively.  FIG. 8  shows input and output voltage level changes of the voltage level shifter. Referring to  FIG. 8 , VOUT3B remains at an analog high voltage high level VDDA during this moment. Similarly, during a time period Td (Td=Twb−Twa), the PMOS transistor  305  is at high impedance state, thus the PMOS transistor  305  is provided as a junction capacitor (i.e., a parasitic capacitor) for maintaining the analog high voltage high level VDDA.  
         [0047]     As one preferred embodiment of the present invention, the two control signals VA and VB, for example, use positive and negative pulses as the controlling signals for a voltage level shifter. A negative pulse of VA and a positive pulse of VB are provided when the input TTL voltage signal VIN changes the state, wherein a width Twa of the negative pulse of VA corresponding to a delay after the rising of VIN. Thus, a narrower pulse width Twa is desired. Furthermore, a width Twb of the positive pulse of VB should be slightly wider than Twa because the time period Td will causes a high impedance state. The slightly wider negative pulse also can prevent from the conducting path constructed by the turning on of the PMOS transistors  303 ,  305  and the NMOS transistors  311 ,  313  and  351  when the input signal VIN is at high voltage level.  
         [0048]     As another preferred embodiment of the present invention, the possible conducting paths, for example, can be constructed by the PMOS transistor  301 , the NMOS transistor  313  and the switch transistor  351  during the changing of state thereof when VIN changes to high voltage level. Referring to  FIG. 3 , the surge of current I( 313 ) is much smaller than the surge of current I( 415 ) because the PMOS transistor  301  and the NMOS transistor  313  are designed to be of any size.  
         [0049]      FIG. 9  is a waveform diagram schematically illustrating the relationships between the input voltages and currents of the transistors of a conventional voltage level shifter and a voltage level shifter according to one preferred embodiment of the present invention. Similarly, referring to  FIG. 9 , as another preferred embodiment of the present invention, a smaller surge is generated in compared with a conventional voltage level shifter since the inverter is constructed by PMOS transistor and NMOS transistors and the time period during the negative rising edge of the input signal.  
         [0050]     Accordingly, two control signals are provided to turn on and off the PMOS transistor and NMOS transistors in the voltage level shifter of the present invention, thus the power consumption during the turning on of the PMOS transistor and NMOS transistors is reduced. Moreover, the current path between the high voltage level and the ground are also broken totally by the two control signals to reduce the power consumption of the analog circuit.  
         [0051]     It will be apparent to those skilled in the art that various modifications and variations can be made to the structure of the present invention without departing from the scope or spirit of the invention. In view of the foregoing, it is intended that the present invention cover modifications and variations of this invention provided they fall within the scope of the following claims and their equivalents.

Technology Category: 5