Patent Document

BACKGROUND OF THE INVENTION 
     The present invention generally relates to a signal processing circuit, and, more particularly, to a signal processing circuit for preventing the pseudo lock of a timing recovery PLL which generates a clock signal having a phase that is substantially coincident with the phase of a recording medium read signal. 
       FIG. 1  is a schematic block diagram of a conventional signal processing circuit  10 . The signal processing circuit  10  includes an analog-to-digital converter (ADC)  11 , a decision feedback equalizer (DFE)  12 , coefficient registers  13  and  14 , a PLL phase error detection circuit  15 , a timing recovery PLL (TR-PLL)  16 , and a control circuit  17 . 
     The ADC  11  samples an analog signal read from a recording medium in accordance with a clock signal CLK supplied from the TR-PLL  16  and converts the analog read signal to a digital read signal. The DFE  12  includes a forward (FW) filter  21 , an adder  22 , a comparator  23 , a shift register  24 , a feedback (FB) filter  25 , an inverter circuit  26 , and switches  27 ,  28 , and  29 . 
     The first and second coefficient registers  13  and  14  are connected to the FW filter  21  via the first switch  27 . The first coefficient register  13  prestores a first filter coefficient (start value) used by the FW filter  21  at startup (i.e., initial read operation). The second coefficient register  14  prestores a second filter coefficient (normal value) used by the FW filter  21  during normal operation (after preamble data has been detected). At startup, the FW filter  21  receives the digital read signal supplied from the ADC  11  and the first filter coefficient via the first switch  27  and filters the digital read signal using the first filter coefficient so that the S/N (signal-to-noise) ratio is maximized. During normal operation, the FW filter  21  filters the digital read signal using the second filter coefficient. 
     The adder  22  receives the filtered digital read signal S 1  from the FW filter  21  and a feedback signal S 2  supplied from the FB filter  25  via the third switch  29  and adds the filtered digital read signal S 1  and an inverse signal of the feedback signal S 2 . That is, the adder  22  functions as a subtractor that subtracts the feedback signal S 2  from the filtered digital read signal S 1 . 
     The comparator  23  compares the voltage of an operation result signal S 3  from the adder  22  and a reference voltage REF and generates a decision signal S 4  of “1” or “0”. The shift register  24  receives the decision signal S 4  supplied from the comparator  23  via the second switch  28  and samples the decision signal S 4  in accordance with the clock signal CLK. Thus, the shift register  24  stores sampling data (i.e., plural pieces of sampled bit data). 
     The data (decision signal S 4 ) stored in the first-bit register of the shift register  24  is output from the shift register  24  as a reproduction data signal. In this manner, the DFE  12  reproduces the data recorded on the recording medium. 
     The FB filter  25  receives the sampling data from the shift register  24 , eliminates inter-code interference contained in the sampling data, and generates the feedback signal S 2 . 
     The PLL phase error detection circuit (hereinafter referred as detection circuit)  15  receives the operation result signal S 3  from the adder  22  and a signal S 6  (the decision signal S 4  from the comparator  23  or an output signal S 5  of the inverter circuit  26 ), detects an error between the phase of the read signal and the phase of the clock signal CLK using the signals S 3  and S 6 , and supplies a control signal S 7  to the TR-PLL  16 . 
     The TR-PLL  16  receives the control signal S 7  from the detection circuit  15  and generates the clock signal CLK that is substantially coincident with the phase of the read signal in accordance with the control signal S 7 . Thus, the shift register  24  samples the decision signal S 4  of the comparator  23  in accordance with the clock signal CLK (the bit transfer rate of the read signal RD). 
     The control circuit  17  controls each of the switches  27  to  29  based on the status of the data signal output from the shift register  24  and the number of bytes read from the start of the read operation. Predetermined preamble data is recorded on the recording medium. The preamble data is pattern data in which a predetermined bit is repeated continuously. Accordingly, the control circuit  17  controls each of the switches  27  to  29  in accordance with a predetermined timing based on the number of bytes of the preamble data. Specifically, the control circuit  17  controls each of the switches  27  to  29  as described below. 
     (1) When the read operation is started, the control circuit  17  switches the first switch  27  to the input of the first coefficient register  13 , the second switch  28  to the output of the comparator  23 , and the third switch  29  to OPEN. The FW filter  21  waveform-shapes the digital read signal from the ADC  11  using the first filter coefficient (start value) from the first coefficient register  13 . The adder  22  supplies the filtered digital signal S 1  from the FW filter  21  to the comparator  23 . The detection circuit  15  supplies the control signal S 4  to the TR-PLL  16  using the filtered digital read signal S 1  and the decision signal S 4 . Accordingly, the TR-PLL  16  performs phase matching of the clock signal CLK using the read signal. 
     (2) When the bit string (“+++” or “−−−” in this case) of the preamble data is supplied from the shift register  24  to the control circuit  17  a predetermined number of times (for example, three times), the control circuit  17  switches the first switch  27  to the input of the second coefficient register  14 , the second switch  28  to the output of the inverter circuit  26 , and the third switch  29  to CLOSED. “+” indicates that the voltage of the sampled read signal RD is higher than the reference voltage REF, and “−” indicates the reverse. 
     The FW filter  21  waveform-shapes the digital read signal from the ADC  11  using the second filter coefficient (normal value) from the second coefficient register  14 . The shift register  24  receives the sampling data of the shift register  24  inverted by the inverter circuit  26  via the second switch  28 . Accordingly, the shift register  24  repeatedly stores the bit string “+++−−−” of the preamble data. Consequently, the data stored in the shift register is initialized as the preamble data. 
     The adder  22  receives the filtered digital read signal S 1  supplied from the FW filter  21  and the feedback signal S 2  supplied from the FB filter  25  via the third switch  29  and adds the filtered digital read signal S 1  and the feedback signal S 2 . 
     (3) The control circuit  17  counts the number of data pieces supplied from the shift register  24  after the control of the aforementioned (2) and enables frequency matching of the TR-PLL  16  after a predetermined number of data pieces (for example, five bytes) are counted. 
     (4) The control circuit  17  counts the number of data pieces supplied from the shift register  24  after the control of the aforementioned (3) and switches (maintains) the first switch  27  to the input of the second coefficient register  14 , the second switch  28  to the output of the comparator  23 , and the third switch  29  to CLOSED. Thus, the TR-PLL  16  performs the phase matching of the clock signal CLK and the DFE  12  outputs a reproduction signal in accordance with the clock signal CLK. 
     However, high speed information reading of recording medium (or the high density of the recording medium) shortens the read period of the preamble data and the phase matching time of the TR-PLL  16 . In other words, the setting change of the FW filter  21 , the on/off control of the feedback loop, the preamble synchronization of the shift register  24 , and the time for initializing the feedback loop by the control circuit  17  are shortened. As a result, the control timing for each of the switches  27  to  29  using the control circuit  17  becomes inaccurate, and the phase matching of the TR-PLL  16  is not performed accurately. Accordingly, valid read data is not obtained. 
     The control circuit  17  determines the control timing for each of the switches  27  to  29  based on the number of preamble data pieces. That is, the control circuit  17  does not perform the timing control until the predetermined number of data pieces is supplied even if the phase of the clock signal CLK and the phase of the read signal are substantially coincident at an early stage. This prolongs the phase matching time of the TR-PLL  16 . 
     Further, phase control advances or delays the phase of the clock signal CLK. If the feedback loop is closed (i.e., the third switch  29  is closed) when phase matching of the clock signal CLK is not completed, the TR-PLL  16  may fall into a pseudo lock condition. Specifically, when the phase matching is not complete, the feedback signal S 2  having a higher value than the desired value is supplied to the adder  22 . In this case, the decision result of the preamble data by the comparator  23  ends in a result (for example, “++−−−−”) that is different from the original decision result. In the decision result, the amount of control for advancing and delaying the phase substantially become equal. As a result, the TR-PLL 16  generates a stable clock signal CLK at a frequency shifted from the frequency of the read signal RD. When the TR-PLL  16  is pseudo-locked, it is necessary to resume the read operation, which delays the read speed. One way to prevent the pseudo lock is to increase the number of preamble data pieces. However, increasing the number of preamble data pieces hinders high-density recording on the recording medium and high-speed reading. 
     It is an object of the present invention to provide a signal processing circuit that prevents pseudo lock of the timing recovery PLL. 
     SUMMARY OF THE INVENTION 
     In one aspect of the present invention, a signal processing circuit includes a decision feedback equalizer for waveform-equalizing a digital signal in accordance with a clock signal and generating the waveform-equalized digital signal. A timing recovery PLL generates the clock signal having a phase which is substantially coincident with the phase of the digital signal based on the phase difference between the digital signal and the clock signal and supplies the clock signal to the decision feedback equalizer. The decision feedback equalizer includes a prefilter for filtering the digital signal and generating a filtered digital signal. A decision circuit adds a feedback signal and the filtered digital signal, generates an addition signal and analyzes the addition signal in accordance with predetermined criteria to generate a decision signal. A shift register samples the decision signal in accordance with the clock signal and storing sampling data. The sampling data stored in the shift register is output from the shift register as the waveform-equalized digital signal. A feedback filter receives the sampling data and generating the feedback signal using the sampling data. A loop control circuit monitors the filtered digital signal and the feedback signal and controls a feedback loop formed by the decision circuit, the shift register, and the feedback filter based on a monitoring result. 
     In another aspect of the present invention, a feedback control of a signal processor method is provided. First, a digital signal is filtered to generate a filtered digital signal. A feedback signal and the filtered digital signal are added to generate the addition signal. The addition signal is analyzed in accordance with predetermined criteria to generate a decision signal. The decision signal is sampled in accordance with a clock signal to store sampling data in a shift register. The feedback signal is generated using the sampling data stored in the shift register. The clock signal, which is substantially coincident with the phase of the digital signal, is generated based on a phase difference between the digital signal and the clock signal. The filtered digital signal and the feedback signal are monitored. Then, whether the feedback signal is fed back to the step of generating the addition signal is selected based on a monitoring result. 
     In yet another aspect of the present invention, a feedback control of a signal processor is provided. First, a digital signal is filtered to generate a filtered digital signal. A feedback signal and the filtered digital signal are added to generate the addition signal. The addition signal is analyzed in accordance with predetermined criteria to generate a decision signal. The decision signal is sampled in accordance with a clock signal to store sampling data in a shift register. The feedback signal is generated using the sampling data stored in the shift register. A first phase difference between the digital signal and the clock signal are generated using the decision signal and a first reference signal. The first reference signal has a first predetermined value at preset control point of the filtered digital signal. Then, the clock signal is generated having a phase which is substantially coincident with the phase of the digital signal, based on a first phase difference. Whether the first phase difference is within a predetermined range is determined. The feedback signal is fed back to the step of generating the addition signal when the first phase difference is within the predetermined range. A second phase difference between the digital signal and the clock signal is generated using the decision signal and a second reference signal. The second reference signal has a second predetermined value at the preset control point preset of the decision signal. Then, the clock signal having a phase which is substantially coincident with the phase of the digital signal is generated based on the second phase difference. 
     Other aspects and advantages of the invention will become apparent from the following description, taken in conjunction with the accompanying drawings, illustrating by way of example the principles of the invention. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       The invention, together with objects and advantages thereof, may best be understood by reference to the following description of the presently preferred embodiment together with the accompanying drawings in which: 
         FIG. 1  is a schematic block diagram of a conventional signal processing circuit; 
         FIG. 2  is a schematic block diagram of a hard disk drive; 
         FIG. 3  is a schematic block diagram of the signal processing circuit of the hard disk drive of  FIG. 2  according to a first embodiment of the present invention; 
         FIG. 4  is a flowchart showing the operation of the signal processing circuit of  FIG. 3 ; and 
         FIG. 5  is a timing diagram describing the operation timing of the signal processing circuit of  FIG. 3 . 
     
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     In the drawings, like numerals are used for like elements throughout. 
       FIG. 2  is a schematic block diagram of a hard disk drive. The hard disk drive  31  is connected to a host computer  32  and records data supplied from the host computer  32  on a recording medium, such as a magnetic disk  33  in response to a write request from the host computer  32 . The hard disk drive  31  reads the data recorded on the magnetic disk  33  in response to a read request from the host computer  32  and supplies the data to the host computer  32 . 
     The hard disk drive  31  includes the magnetic disk  33 , first and second motors M 1  and M 2 , a head device  34 , a signal processing circuit  35 , a servo circuit  36 , a microprocessor unit (MPU)  37 , a memory device (RAM)  38 , a hard disk controller (HDC)  39 , and an interface circuit  40 . Each of the circuits  35  to  40  is connected via a bus  41 . 
     The magnetic disk  33  is driven by the first motor M 1  at a constant rotational speed. The movement of the head device  34  in the radial direction of the magnetic disk  33  is controlled by the second motor M 2 . The head device  34  reads the information recorded on the magnetic disk  33  and supplies an analog read signal RD to the signal processing circuit  35 . 
     The signal processing circuit (called a read/write channel IC)  35  samples the analog read signal RD and converts the analog read signal RD to a digital read signal. The signal processing circuit  35  also decodes the digital read signal. 
     The servo circuit  36  receives the digital read signal from the signal processing circuit  35 , and based on servo information contained in the digital read signal, controls the second motor M 2  to move the head device  34  and also controls the first motor M 1  for rotating the magnetic disk  33  at a constant speed. 
     The MPU  37  analyzes a read/write command supplied from the host computer  32  in accordance with a program prestored in the RAM  38  and supplies a control signal to the HDC  39 . The HDC  39  controls the signal processing circuit  35  and the servo circuit  36  in accordance with the control signal from the MPU  37 . 
     The HDC  39  receives a data signal decoded from the signal processing circuit  35 , performs ECC (error correcting code) processing on the decoded data in a sector unit, and supplies error corrected data to the interface circuit  40 . The interface circuit  40  converts the error corrected data from the HDC  39  to data conforming to a predetermined communication protocol and supplies read data to the host computer  32 . 
       FIG. 3  is a schematic block diagram of the signal processing circuit  35 . The signal processing circuit  35  includes the analog-to-digital converter (ADC)  11 , a decision feedback equalizer (DFE)  51 , a feedback loop control circuit  52 , a PLL phase error detection circuit  53 , a timing recovery PLL (TR-PLL)  54 , and a sequence control circuit  55 . The DFE  51  includes a forward (FW) filter (prefilter)  61 , an adder  62 , a shift register  63 , a feedback (FB) filter (feedback filter)  64 , and a switch  65 . 
     The ADC  11  samples the analog signal read from the recording medium  33  in accordance with a clock signal supplied from the TR-PLL  54  and converts the analog read signal RD to a digital read signal. The FW filter  61  receives the digital read signal from the ADC  11  and waveform-shapes the digital read signal in response to a read gate signal RG supplied from the sequence control circuit  55  so that the S/N ratio of the digital read signal is maximized. The FW filter  61  is a digital filter having a predetermined transfer characteristic. 
     The adder  62  receives the filtered digital read signal S 11  from the FW filter  61  and a feedback signal S 12  from the FB filter  64  and adds the filtered digital read signal S 11  and an inverse signal of the feedback signal S 12 . In other words, the adder  62  functions as a subtractor that subtracts the feedback signal S 12  from the filtered digital read signal S 11 . The adder  62  further compares the calculation result and a reference voltage REF (not illustrated) and supplies a decision signal S 13  of either “1” or “0” to the shift register  63 . 
     The shift register  63  samples the decision signal S 13  in accordance with the clock signal CLK and stores the sampling data. Hence, the shift register  63  stores plural pieces of sampled bit data. 
     The data (decision signal S 13 ) stored in the first-bit register of the shift register  63  is output from the shift register  63  as a reproduction data signal. The output data is the data recorded on a recording medium, representing the data stored on the recording medium  33 . In this manner, the DFE  51  reproduces the data stored on the recording medium  33 . After the reproduction data signal is decoded, it is supplied to the HDC  39 . 
     The FB filter  64  receives the sampling data from the shift register  63 , eliminates inter-code interference contained in the sampling data, and supplies the feedback signal S 12  to the adder  62  via the switch  65 . 
     The PLL phase error detection circuit (hereinafter referred as the detection circuit)  53  receives a control signal K 4  from the feedback loop control circuit  52 , the addition signal S 13  from the adder  62 , and first and second reference signals REF 1  and REF 2 , detects an error between the phase of the read signal and the phase of the clock signal CLK generated by the TR-PLL  54 , and supplies a control signal K 1  to the TR-PLL  54  in accordance with the detection result. The first reference signal REF 1  has a value preset based on the ideal preamble read signal RD at a specific point where the signal S 11  changes from 0 to 1 or from 1 to 0. The second reference signal REF 2  has a value preset based on the ideal preamble read signal RD at a specific point of the decision signal S 13  from the adder  62  after the feedback loop has been closed. The value of the second reference signal REF 2  is preferably less than the value of the first reference signal REF 1 . 
     The TR-PLL  54  generates the clock signal CLK having a phase that is substantially coincident with the phase of the read signal RD in accordance with the control signal K 1  from the detection circuit  53  and supplies the clock signal CLK to the shift register  63  and the ADC  11 . The shift register  63  samples the decision signal S 13  supplied from the adder  62  in accordance with the clock signal CLK (bit transfer rate of the read signal RD) and stores the sampling data (recording data of the magnetic disk  33 ). 
     The feedback loop control circuit (hereinafter referred as the loop control circuit)  52  receives the sampling data signal from the shift register  63  and the filtered digital signal S 11  from the FB filter  61  and controls the switch  65  (feedback loop of the DFE  51 ), the detection circuit  53 , and the TR-PLL  54  in response to an enable signal ENB. The loop control circuit  52  specifies a control point based on the sampling data signal from the shift register  63  and monitors the value of the filtered digital signal S 11  and the value of the feedback signal S 12  at the control point. The loop control circuit  52  controls the feedback loop, the phase comparison gain of the detection circuit  53 , and the TR-PLL  54  based on the monitoring result at the control point. 
     The loop control circuit  52  calculates an “FW-FB” value by subtracting the value of the feedback signal S 12  (FB) from the value of the filtered digital signal S 11  (FW). The loop control circuit  52  further specifies a control point where the sampling data signal changes from 0 to 1 or from 1 to 0 and preferably always monitors at the control point whether the “FW-FB” value is within a predetermined range. When the “FW-FB” value is within the predetermined range, a control signal K 2  is supplied to the switch  65 . The switch  65  (feedback loop of the DFE  52 ) is turned on/off in accordance with the control K 2 . The “FW-FB” value at the control point indicates the direction (leading or delay) of a phase shift. In other words, when the direction of the phase of the sampling data signal at the control point is substantially coincident with the direction of the phase indicated by the “FW-FB” value, the feedback loop is closed. In this manner, the pseudo lock of the TR-PLL  54  is prevented by the loop control circuit  52 . 
     The “FW-FB” value at the control point corresponds to the amount of phase shift. The loop control circuit  52  closes the feedback loop in accordance with the amount of phase shift without waiting for the input of the predetermined number of data pieces as the prior art. Accordingly, control is started sooner, and the read time is shortened. 
     The loop control circuit  52  supplies a control signal K 3  to the TR-PLL  54  based on the monitoring result. The TR-PLL  54  starts the phase matching of the clock signal CLK in response to the control signal K 3  from the loop control circuit  52  when the feedback loop is closed. Accordingly, the phase matching time of the TR-PLL  54  is shortened. 
     The loop control circuit  52  supplies the control signal K 4  to the detection circuit  53  based on the monitoring result. The detection circuit  53  performs a phase comparison with a higher phase comparison gain than that during normal operation in response to the control signal K 4 . In other words, the TR-PLL  54  supplies the control signal K 4  to the TR-PLL  54  so that the amount of control of the TR-PLL  54  that corresponds to the phase error increases (the amount of control of phase matching increases). This shortens the phase matching time of the TR-PLL  54 . 
     The loop control circuit  52  includes an adder  66  and a comparator  67 . The adder  66  receives the filtered digital signal S 11  and the feedback signal S 12  and adds the filtered digital signal S 11  and the inverse signal of the feedback signal S 12 . In other words, the adder  66  functions as a subtractor that subtracts the feedback signal S 12  from the filtered digital signal S 11 . The comparator  67  receives an operation result value “FW-FB” from the adder  66  and the sampling data from the shift register  63  and compares the operation result value and decision values min and max. The decision values min and max are prestored in the comparator  67 . The decision value min is the minimum value in the predetermined range, and the decision value max is the maximum value in the predetermined range. The comparator  67  determines whether the operation result value “FW-FB” is within the range set by the decision values min and max and outputs the control signals K 2  to K 4  based on the decision result. 
     The detection circuit  53  receives the control signal K 4  and the first and second reference signals REF 1  and REF 2 . The first and second reference signals REF 1  and REF 2  correspond to the phase comparison gain. As described above, the value of the second reference signal REF 2  is preferably less than the value of the first reference signal REF 1 . Accordingly, the phase comparison gain using the first reference signal REF 1  is higher than the phase comparison gain using the second reference signal REF 2 . The detection circuit  53  detects a phase error using the first and second reference signals REF 1  and REF 2  and supplies the pulse signal (control signal) K 1 , which corresponds to the phase error, to the TR-PLL  54 . 
     The TR-PLL  54  includes a loop filter  68  and a voltage-controlled oscillator (VCO)  69 . The loop filter  68  receives the pulse signal K 1  from the detection circuit  53 , smoothes the pulse signal K 1 , and supplies a direct current voltage signal K 11  to the VCO  69 . In other words, the loop filter  44  raises and drops the voltage of the direct current voltage signal K 11  in accordance with the phase difference signal K 1  between the addition signal S 13  and the clock signal CLK. The VCO  69  outputs the clock signal CLK having a frequency which corresponds to the direct current voltage signal K 11  to the ADC  11 , the detection circuit  53 , and the shift register  63 . In other words, the VCO  69  performs phase matching in accordance with the direct voltage signal K 11  so that the frequency of the clock signal CLK is substantially coincident with the frequency of the read signal RD. 
     The sequence control circuit  55  receives a read control signal from the MPU  37  and is activated in response to the read control signal. The activated sequence control circuit  55  supplies the read gate signal RG to the FW filter  61  in accordance with the predetermined read sequence, supplies the enable signal ENB to the loop control circuit  52 , and supplies a control signal TR to the detection circuit  53  and the loop filter  68 . 
     Referring now to  FIGS. 4 and 5 , the operation of the signal processing circuit  35  will be described.  FIG. 4  is a flowchart describing the operation of the signal processing circuit  35 .  FIG. 5  is a timing chart of the operation of the signal processing circuit  35 . 
     First, when a control signal is supplied from the MPU  37  to the sequence control circuit  55 , a read gate signal RG High is supplied to the FW filter  61  at a time T 1  (step  1 ). The FW filter  61  filters the digital read signal from the ADC  11  in response to the read gate signal RG High and supplies the filtered data signal S 11  to the adder  62 . At this time, the loop control circuit  52  supplies the control signals K 2  to K 4  to the switch  65 , the loop filter  68 , and the detection circuit  53  in order to open the feedback loop and to turn off the PLL control (step  2 ). Thus, the digital read signal S 11  of the preamble data output from the FW filter  61  is supplied to the shift register  63  via the adder  62 , and the code bit of the preamble data is stored in the shift register  63 . 
     Subsequently, an enable signal ENB High is supplied from the sequence control circuit  55  to the loop control circuit  52  at a time T 2  (step  3 ). The loop control circuit  52  supplies the control signal K 4  to the detection circuit  53  in response to the enable signal ENB High. The detection circuit  53  supplies the control signal K 1 , which corresponds to a phase error, to the loop filter  68  in response to the control signal K 4  using the first reference signal REF 1  and the decision signal S 13  (step  4 ). The loop filter  68  sets a filter constant, which corresponds to Feedback Loop open, in response to the control signal K 1  (FB-OFF setting). The control signal K 1  is generated by the high phase comparison gain of the detection circuit  53  in accordance with the control from the loop control circuit  52 . Accordingly, the amount of control (e.g. high level pulse width, or duty ratio) of the control signal K 1  is relatively high. The loop filter  68  smoothes the control signal K 1  and supplies the direct current voltage signal K 1  to the VCO  69 . At this time, because the amount of control of the control signal K 1  is relatively high, the loop filter  68  supplies the direct current voltage signal K 11  to the VCO  69  for a longer time than the normal operation. Accordingly, the VCO  69  performs the phase matching of the clock signal CLK in a shorter time than for a normal operation. Thus, the TR-PLL  54  quickly performs the phase matching of the clock signal CLK based on the phase difference between the addition signal S 13  (code decision result or reproduction result) of the adder  62  and the clock signal CLK. 
     Subsequently, the comparator  67  of the loop control circuit  52  compares the operation result “FW-FB” value of the adder  66  and the decision values min and max and determines whether the “FW-FB” value is within a range specified by the decision values min and max at the predetermined control point (step  5 ). 
     When the “FW-FB” value is not within the range, the loop control circuit  52  repeats step  5  in the predetermined control point until the “FW-FB” value is within the range. When the “FW-FB” value is within the predetermined range at the time T 3 , the comparator  67  supplies the control signal K 2  High to the switch  65 . The switch  65  is turned on in response to the control signal K 2  High, and the feedback loop is closed (step  6 ). 
     The detection circuit  53  receives the control signal K 4 , which corresponds to the control signal K 2  High, from the comparator  67  and detects an error using the second reference signal REF 2  and the decision signal S 13 . The loop filter  68  receives the control signal K 3 , which corresponds to the control signal K 2  High, from the comparator  67  and sets a constant that corresponds to Feedback Loop close (FB-ON setting). Thus, the TR-PLL  54  performs the normal phase matching operation (step  7 ). 
     At time T 4  when a predetermined period has elapsed from the time T 3 , the sequence control circuit  55  supplies a control signal TR High to the detection circuit  53  and the loop filter  68  (step  8 ). The TR-PLL  54  controls a PLL loop in response to the control signal TR High (TR CON). 
     The detection circuit  53  updates or follows up the phase error detection in response to the control signal TR using the second reference signal REF 2  and the decision signal S 13 . The loop filter  68  sets a loop constant that corresponds to the follow-up operation (follow-up setting) (step  9 ). This loop constant corresponds to a sink byte (SB) and recording data (DATA) read following the preamble data. The value of the loop constant changes the frequency of the clock signal CLK to a predetermined value. 
     Next, the sequence control circuit  55  supplies the sink byte detection signal to the MPU  37  when the sink byte (SB) is detected. The MPU  37  handles the bit data supplied from the signal processing circuit  35  following the sink byte as recording data in accordance with the sink byte detection signal and processes the recording data (step  10 ). 
     (1) In the embodiment, the digital read signal S 11  and the feedback signal S 12  are monitored by the loop control circuit  54 , and the feedback loop is controlled based on the monitoring result. Accordingly, the pseudo lock of the timing recovery PLL  54 , which performs the phase matching of the clock signal CLK using the digital read signal S 11  and the feedback signal S 12 , is prevented. 
     (2) The minimum decision value min and the maximum decision value max in the predetermined range are prestored in the comparator  67 . At the specific control point of the sampling data of the shift register  63 , when the difference between the digital read signal S 11  and the feedback signal S 12  is within the predetermined range, the feedback loop is closed. At this time, the value of the addition signal output from the adder  66  is substantially the same as the value of the decision signal S 13  output from the adder  62 . Accordingly, when the feedback loop is closed, the value of the decision signal S 13  is within the predetermined range. This sets a desired initial value in the shift register  63  and suppresses the excess response of the feedback loop. As a result, the phase matching time of the TR-PLL  54  is shortened. 
     (3) The amount of the preamble data recorded on the magnetic disk  33  is reduced by shortening the phase matching time of the TR-PLL  54 . This allows the recording area of the recording data and the recording density of the magnetic disk  33  to be increased. 
     It should be apparent to those skilled in the art that the present invention may be embodied in many other specific forms without departing from the spirit or scope of the invention. Therefore, the present examples and embodiment are to be considered as illustrative and not restrictive and the invention is not to be limited to the details given herein, but may be modified within the scope and equivalence of the appended claims.

Technology Category: 5