Patent Abstract:
A circuit for fencing input signals to circuits in a voltage island when switching between a normal and a standby power supply is disclosed. A voltage detector detects the switch over in power source and generates a power switch signal. The power switch signal is synchronized to a standby clock and a normal clock. The synchronized standby clock signal is delayed by a counter to allow circuit stabilization. The normal and standby clock signals are logically combined and used to fence input signals to the circuits on the voltage islands.

Full Description:
FIELD OF THE INVENTION 
     The present invention relates to the field of a power supply circuits; more specifically, it relates to circuit and method for switching between normal and standby power supplies in an integrated circuit. 
     BACKGROUND OF THE INVENTION 
     In order to conserve power, semiconductor devices often are designed to allow shutdown of all but a few critical circuits that are kept powered in order continue critical functions and to speed up turn on of the device when it is re-powered or not to lose data or the last state of the device before power down. These critical circuits are place on voltage islands. 
     Current technologies allow voltage islands to exist within dies. Different portions of the die can be powered down while other portions, typically powered isolated logic blocks or voltage islands, need to maintain power. In some cases powering off and powering on do not impact different voltage islands. However, in critical cases, for example, a real time clock, signals on the connections from logic circuits in the portions of the die that are powered down can interfere with the function of logic circuits on a voltage island that is powered up. Voltage island logic circuits are most vulnerable during the times that the die first powers down, and the voltage island switches from normal to standby power, during the time the die is powered down and the voltage island is running on standby power and during the time the die is powered up and the voltage island is switched back to normal power. As a result creating a safe isolation method and restoration mechanism for the connections to the voltage islands is important to avoid malfunctions of the die during power down, standby and power up. Fencing is the name coupled to a method of isolation and restoration of voltage islands. 
     Generally, it is only the inputs to a voltage island that are of concern during the transition periods between normal and standby power and the standby period. Some inputs need to be isolated, such as test clocks, control signals, data buses and scan control signals. Some inputs need to be isolated and glitchless, such as clock-ins, inputs to self timed logic circuits and other circuits sensitive to input signal edges. Glitches occur when signals turn on or turn off. Glitches can make latches switch, so the data stored on the latch is wrong or they can make the latch become meta-stable which requires a significant amount of time to resolve. 
     FIG. 1 is a diagram illustrating voltage islands on a semiconductor die. In FIG. 1, die  100  is comprised of a plurality of input/output (I/O) pads  105 , wire I/O pads  106  and a circuit area  110 . Circuit area  110  includes a first voltage island  115 , a second voltage island  120 , a clock circuit  125  and a plurality of electrostatic discharge isolation/receiver (ESD/R) circuits  130  and ESD circuits  131 . I/O pads  105  are connected to ESD/R circuits  130 . Wire I/O pads  106  are connected to ESD circuits  131 . ESD circuits  131  are not connected to VDD. A portion of I/O pads  105  provides input signals  135  to circuits in circuit area  110 . A portion of I/O pads  105  provide output signals  140  from circuits in circuit area  110 . A portion of I/O pads  105  provide input signals  145  to circuits in voltage island  115 . A portion of I/O pads  106  provide input signals  146  to voltage island  115 . A portion of I/O pads  106  provide input signals  147  to clock circuit  125 . A portion of I/O pads  105  provide output signals  150  from circuits in voltage island  115 . Voltage island  115  has inputs  155  from and outputs  160  to circuits in circuit area  110 . Voltage island  115  also has an input  165  from clock circuit  125  and an output  170  to voltage island  120 . Voltage island  120  has inputs  175  from and outputs  180  to circuits in circuit area  110 . Inputs  145 ,  155 ,  165  and  175  require fencing for safe switch over from normal to standby power and back again. Inputs  146  and  147  do not require fencing as there is no connection to VDD 
     An important requirement for fencing is to allow enough time between the start of power down/up and the completion of power down/up operations to ensure the die enough time to become stable or to reset properly. 
     SUMMARY OF THE INVENTION 
     A first aspect of the present invention is a circuit for fencing input signals to circuits in a voltage island when switching between a normal power supply and a standby power supply, comprising: a voltage detector outputting a power sense signal in response to a fall to a first voltage value from a reference value or a rise to a second voltage value from the reference value of the voltage of the normal power supply; a standby clock generating a standby clock signal; a standby clock synchronizing circuit receiving the power sense signal and the standby clock signal, synchronizing the power sense signal to the standby clock domain and outputting a standby clock synchronized power sense signal; a counter receiving the standby clock synchronized power sense signal and the power sense signal, adding a delay to the standby clock synchronized power sense signal and outputting a delayed standby clock synchronized power sense signal; a normal clock synchronizing circuit receiving the delayed standby clock synchronized power sense signal, synchronizing the delayed standby clock synchronized power sense signal to the normal clock domain and outputting a delayed normal clock synchronized power sense signal; and fencing logic circuit receiving the delayed normal clock synchronized power sense signal and forcing the input signals high or low synchronously with the delayed normal clock synchronized power sense signal. 
     A second aspect of the present invention is a circuit for fencing input signals to circuits in a voltage island when switching between a normal power supply and a standby power supply, comprising: a voltage detector outputting a power sense signal in response to a fall to a first voltage value from a reference value or a rise to a second voltage value from the reference value of the voltage of the normal power supply; a standby clock generating a standby clock signal; a standby clock synchronizing circuit receiving the power sense signal and the standby clock signal, synchronizing the power sense signal to the standby clock domain and outputting a standby clock synchronized power sense signal; a counter receiving the standby clock synchronized power sense signal and the standby clock signal, adding a delay to the standby clock synchronized power sense signal and outputting a delayed standby clock synchronized power sense signal; and fencing logic circuit receiving the delayed standby clock synchronized power sense signal and forcing the input signals high or low synchronously with the delayed standby clock synchronized power sense signal. 
     A third aspect of the present invention is a method for fencing input signals to circuits in a voltage island when switching between a normal power supply and a standby power supply, comprising: outputting a power sense signal in response to a fall to a first voltage value from a reference value or a rise to a second voltage value from the reference value of the voltage of the normal power supply; generating a standby clock signal; synchronizing the power sense signal to the standby clock domain to create a standby clock synchronized power sense signal; adding a delay to the standby clock synchronized power sense signal to create a delayed standby clock synchronized power sense signal; synchronizing the delayed standby clock synchronized power sense signal to the normal clock domain to create a delayed normal clock synchronized power sense signal; and forcing the input signals high or low synchronously with the delayed normal clock synchronized power sense signal. 
     A fourth aspect of the present invention is a method for fencing input signals to circuits in a voltage island when switching between a normal power supply and a standby power supply, comprising: outputting a power sense signal in response to a fall to a first voltage value from a reference value or a rise to a second voltage value from the reference value of the voltage of the normal power supply; generating a standby clock signal; synchronizing the power sense signal to the standby clock domain to create a standby clock synchronized power sense signal; adding a delay to the standby clock synchronized power sense signal to create a delayed standby clock synchronized power sense signal; and forcing the input signals high or low synchronously with the delayed standby clock synchronized power sense signal. 
    
    
     BRIEF DESCRIPTION OF DRAWINGS 
     The features of the invention are set forth in the appended claims. The invention itself, however, will be best understood by reference to the following detailed description of an illustrative embodiment when read in conjunction with the accompanying drawings, wherein: 
     FIG. 1 is a diagram illustrating voltage islands on a semiconductor die; 
     FIG. 2 is a block diagram of a circuit for fencing signals to a voltage island according to a first embodiment of the present invention; 
     FIG. 3 is a schematic diagram of the circuit illustrated in FIG. 2 according to the first embodiment of the present invention; 
     FIG. 4 is a schematic diagram of counter  225  of the circuit illustrated in FIG. 3 according to the first embodiment of the present invention; 
     FIGS. 5 and 6 are schematic diagrams of force to logical zero circuit  350  and force to logical one circuit  355  of fencing logic circuit  245  of the circuit illustrated in FIG. 3 according to the present invention; 
     FIG. 7 is a timing diagram illustrating the timing between the VDD, POS and PS-Sync signals of the circuit illustrated in FIG. 2 according to the first embodiment of the present invention; 
     FIG. 8 is a timing diagram of the circuit of the circuit illustrated in FIG. 3 according to the first embodiment of the present invention; 
     FIG. 9 is an expanded view of section  500  of the timing diagram illustrated in FIG. 9 according to the first embodiment of the present invention; 
     FIG. 10 is an expanded view of section  510  of the timing diagram illustrated in FIG. 9 according to the first embodiment of the present invention; 
     FIG. 11 is a flowchart illustrating the initial power up of AVDD according to the first embodiment of the present invention; 
     FIG. 12 is a flowchart illustrating power down of VDD according to the first embodiment of the present invention; 
     FIG. 13 is a flowchart illustrating the power up of VDD according to the first embodiment of the present invention; 
     FIG. 14 is a schematic diagram of a fencing circuit  640  for fencing signals to a voltage island according to a second embodiment of the present invention; 
     FIG. 15 a schematic diagram of the counter  720  of the circuit illustrated in FIG. 14 according to the second embodiment of the present invention; 
     FIG. 16 is a plot of the VDD signal vs. time according to the second embodiment of the present invention; and 
     FIG. 17 is a flowchart illustrating power down of VDD according to the second embodiment of the present invention; and 
     FIG. 18 is a flowchart illustrating the power up of VDD according to the second embodiment of the present invention 
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     The circuit and method of fencing of the present invention protects power isolated logic blocks, which may be application specific integrated circuits (ASIC) or cores or voltage island (cores) when the rest of the die is powered down/on by generating a power sense signal that detects a threshold drop in VDD. When VDD is turned off or restored the power sense signal is delayed a specified amount of time. This delay allows enough time for the die to become stable or to be reset. The circuit uses a glitchless voltage detector that contains some hysteresis between the falling and rising of VDD. The output of the voltage detector is guaranteed to remain low when power falls to a first predetermined fraction of VDD (or a reference voltage), for example 80%. A 32 KHz oscillator, powered by standby power during power down, is used for clocking the logic. All signals to the voltage island that will lose power are forced (fenced) to their logical functional values so in they are in their functional mode when they reach the minimum technology operating voltage. 
     FIG. 2 is a block diagram of a circuit for fencing signals to a voltage island according to a first embodiment of the present invention. In FIG. 2, fencing circuit  200  comprises a voltage detector  205  and a 32 KHz clock  210 . The outputs of voltage detector  205 , a power sense signal (POS), and 32 KHz clock  210 , a standby clock signal (CLK32), are both coupled to inputs of a 32 KHz synchronizing logic circuit  215 . In this example, the standby clock is a 32 KHz clock. An input of voltage detector  205  is also coupled to VDD. Voltage detector  205  detects when VDD drops to the first predetermined fraction of VDD or rises a second predetermined fraction of VDD (or the reference voltage), for example 81% and then generates the POS signal which is coupled a first input of 32 KHz synchronizing logic circuit  215  and a first input of AND gate  220 . Note the second predetermined value of VDD must be different than the first predetermined fraction of VDD. It may be higher or lower. 32 KHz clock  210  is a “safe clock” that provides a lower power, 32 KHz signal (CLK32) directly to 32 KHz synchronizing logic circuit  215 , a counter  225 , a latch  230  and indirectly to voltage island circuits and for running state machines and other functions that need to be on all the time. CLK32 is coupled to a second input of 32 KHz synchronizing logic circuit  215 , a second input of counter  225  and the clock input of latch  230 . 
     The output of 32 KHz synchronizing logic circuit  215 , a standby clock synchronized power sense signal (POS SYNC), is coupled to a second input of counter  225  and a first input of an AND gate  235 . AND gates  220  and  235  and latch  230  comprise combinational logic circuit  237 . 32 KHz synchronizing logic circuit  215  aligns the POS signal to the CLK32 edge to output the POS SYNC signal. 
     The output of counter  225 , a delayed standby clock synchronized power sense signal (PS DLY), is coupled to a data input of latch  230  and a second input of AND gate  235 . Counter  225  imposes a delay on the POS SYNC signal. The output of latch  230  is coupled back to counter  225  and to a second input of AND gate  220 . Latch  230  adds a further delay to the PS DLY signal and outputs a further delayed standby clock synchronized power sense signal (PS DLY PLUS). The PS DLY PLUS signal is coupled back to counter  225  and to the second input of AND gate  220   
     In this example, the normal clock is a 66 MHz clock signal (CLK66) which is coupled to a first input of a 66 MHz synchronizing logic circuit  240  and to a fencing logic circuit  245 . AND gate  220  combines the PS DLY PLUS signal with the POS signal to output a PS COUNT signal, which is coupled to a second input of 66 MHz synchronizing logic circuit  240 . The output of 66 MHz synchronizing logic circuit  240 , a delayed normal clock synchronized power sense signal (PS SYNC1), is coupled a third input of AND gate  235 . 66 MHz synchronizing logic circuit  240  is also coupled to a fenced clock signal FTS described below. PS SYNC1 is a glitchless signal. The PS SYNC1 signal is also coupled to the third input of AND gate  235 . AND gate  235  combines the PS DLY signal, the POS SYNC signal and the PS SYNC1 signal to output a PS SYNC signal to fencing logic circuit  245 . 
     Power supply  247  comprises VDD coupled to the input of a diode  250 A and a standby power source (STBY PWR) coupled to the input of a diode  250 B; the outputs of diodes  250 A and  250 B being tied together at output node  255  (AVDD.) Output node  255  is a wire I/O pad. AVDD is VDD when the circuit is in active mode or is STBY PWR when the circuit is in standby mode. Node  255  is coupled to an input of 32 KHz clock  210  and to fencing logic circuit  245 . 
     A PS TEST signal and a plurality of test signals represented by TA and TB are coupled to fencing logic circuit  245 . A plurality of logic signals represented by A and B are coupled to fencing logic circuit  245  as well. Fencing logic circuit  245  converts the CLK66 signal into a fenced clock signal F CLK, the TA and TB into fenced test signals FTA and FTB (represented by FTS) and logic signals A and B into fenced logic signals FA and FB. Fenced signals FA, FB, F CLK, FTA and FTB are forced to either a logical one or logical zero state. FA and FTA represent signals fenced to a zero logic state and FB and FTB represent signals fenced to a logical one state. 
     32 KHz synchronizing logic circuit  215 , counter  225 , fencing logic circuit  245  and AND gates  220  and  235  and latch  230  are located in a voltage island  260 . Voltage island  260  is an AVDD region of a semiconductor die and all circuits in the AVDD region are powered by AVDD power lines instead of VDD power lines. 
     An example application of fencing circuit  200  is for a Real Time Clock with the STBY PWR being supplied by a battery. Once the real time clock is initialized power to it must be maintained. It is impractical to keep the entire chip powered up so power is supplied to the real time clock only. The present invention allows a Real Time Clock to be placed on voltage island  260  instead of being external to the semiconductor die. 
     FIG. 3 is a schematic diagram of the circuit illustrated in FIG. 2 according to the first embodiment of the present invention. In FIG. 3, voltage detector  205  is comprised of a resistor  265 A coupled in series to a resistor  265 B and a resistor  265 C coupled in series to a resister  265 D. Resistors  265 A and  265 C are coupled to VDD and resistors  265 B and  265 D are coupled to ground (GND). The negative input of an amplifier  270  is coupled between resistors  265 A and  265 C. The positive input of amplifier  270  is coupled between resistors  265 B and  265 D. An inverter  275  is coupled to the output of amplifier  270 . The output of inverter  275  is the POS signal. Hysteresis is introduced into voltage detector  205  by selection of values for resistors  265 A through  265 D. 
     32 KHz clock  210  is comprised of a 32K oscillator coupled to a crystal  285 . One side of crystal  285  is coupled to a first input of 32K oscillator  280  and the opposite side of crystal  285  is coupled to a second input of the 32K oscillator. A capacitor  290 A is coupled between the first input of 32K oscillator  280  and GND and a capacitor  290 B is coupled between the second input of the 32K oscillator and GND. The output of 32K oscillator  280  is the CLK32 signal. Nodes  291 A and  291 B are wire I/O pads. 32 KHz synchronizing logic circuit  215  is comprised of an inverter element  295 , a latch  300  and a latch  305 . Latches  300  and  305  are flip-flops (edge triggered). The output of 32K oscillator  280  (CLK32) is coupled to clock inputs of latches  300  and  305 , counter  225  and the clock input of latch  230 . The output of inverter  275  of voltage detector  205  (POS) is coupled to a data input of latch  300 . The output of latch  300  is coupled to the data input of latch  305 . The output of latch  305  is the first output (POS SYNC) of 32 KHz synchronizing logic circuit  215 . 
     66 MHz synchronizing logic circuit  240  is comprised of latches  310 ,  315  and  320 . Latches  310  and  315  are flip-flops (edge triggered) while latch  320  is a transparent (level sensitive) latch. The data input of latch  310  is coupled to the output of AND gate  220  (PS COUNT). The output of latch  310  is coupled to the input of latch  315  and the output of latch  315  is coupled to the input of latch  320 . The output of latch  320  (PS SYNC1) is coupled to the input of AND gate  235 . The clock input of each of latches  310 ,  315  and  320  are coupled to the CLK66 signal. Latches  310 ,  315  and  320  are also coupled to the FTS signal. Latches  310  and  315  synchronize the PS COUNT signal to the 66 MHz clock domain. Latch  320  synchronizes the PS COUNT signal to the low phase of the 66 MHz clock domain. 
     Fencing logic circuit  245  is comprised of an AND gate  325 , an AND gate  330 , an OR gate  335 , an OR gate  345 , an inverter  347 , a force to logical zero circuit  350  and a force to logical one circuit  355 . The CLK66 signal is coupled to a first input of AND gate  325 . The PS TEST signal is coupled to a first input of OR gate  335 . PS TEST is a wire I/O pad signal. The CA signal is coupled to a first input of AND gate  330 . The CB signal is coupled to a first input of OR gate  325 . A second input of AND gate  325  is coupled to a second input of OR gate  335  and to PS SYNC. The output of AND gate  325  is the F CLK signal. The output of OR gate  335  is coupled to a second input of AND gate  330  and the input of inverter  347 . The output of inverter  347  is coupled to a second input of OR gate  345 . The output of AND gate  330  is the FCA signal. The output of OR gate  345  is the FCB signal. The output of AND gate  235  is coupled to first inputs of force to logical zero circuit  350  and force to logical one circuit  355 . The A signal is coupled to a third input of force to logical zero circuit  350  and the B signal is coupled to a third input of force to logical one circuit  355 . 
     FIG. 4 is a schematic diagram of counter  225  of the circuit illustrated in FIG. 3 according to the first embodiment of the present invention. In FIG. 4, the CLK32 signal is coupled to the clock input of latches  360 ,  365 ,  370 , and  375 . The output of latch  360  is a COUNT 0 signal. The output of latch  360  is coupled to a first input of an AND gate  380  and to a first input of an ADDER  385 . The output of latch  365  is a COUNT 1 signal. The output of latch  365  is coupled to a second input of AND gate  380  and to a second input of ADDER  385 . The output of latch  370  is a COUNT 2 signal. The output of latch  370  is coupled to a third input of AND gate  380  and to a third input of ADDER  385 . The output of latch  375  is a COUNT 3 signal. The output of latch  375  is coupled to a fourth input of AND gate  380  and to a fourth input of ADDER  385 . The output of AND gate  380  is the PS DLY signal. The output of AND gate  380  is also coupled to a first input of each of OR gates  390 ,  395 ,  400  and  405 . The PS DLY PLUS signal from latch  230  is coupled to a second input of each of OR gates  390 ,  395 ,  400  and  405 . ADDER  385  has four outputs. A first output (INC 0) of ADDER  385  is coupled to a third input of OR gate  390 . A second output (INC 0) of ADDER  385  is coupled to a third input of OR gate  395 . A third output (INC 2) of ADDER  385  is coupled to a third input of OR gate  400 . A fourth output (INC 3) of ADDER  385  is coupled to a fourth input of OR gate  405 . The POS SYNC signal is couple to a first input of each of AND gates  410 ,  415 ,  420  and  425 . The output of OR gate  390  is coupled to a second input of AND gate  410 . The output of OR gate  395  is coupled to a second input of AND gate  415 . The output of OR gate  400  is coupled to a second input of AND gate  420 . The output of OR gate  405  is coupled to a second input of AND gate  425 . The output of AND gate  410  is coupled to a data in of latch  360 . The output of AND gate  415  is coupled to a data in of latch  365 . The output of AND gate  420  is coupled to a data in of latch  370 . The output of AND gate  425  is coupled to a data in of latch  375 . 
     In operation, counter  225  increments while the POS SYNC signal is high until a maximum count is reached. Counter  225  functions only during power-up, that is, when VDD is turned back on. When the maximum count is reached, the counter will stop incrementing. The counter is initialized to zero when the POS SYNC is low and will remain in the zero state until POS SYNC transitions to high. Counter  225  is, in the present example, a four bit counter with a maximum count of 16. With a 32 KHz clock a 500 microsecond delay is realized. Latches  360 ,  365 ,  370  and  375  store the current count. To increase the delay additional latches are added. For example, 5 latches yields a maximum count of 5 2  (32) and a delay of one millisecond. 
     FIGS. 5 and 6 are schematic diagrams of force to logical zero circuit  350  and force to logical one circuit  355  of fencing logic circuit  245  of the circuit illustrated in FIG. 3 according to the present invention. In FIG. 5, force to logical zero circuit  350  is comprised of PFETs  430 ,  435  and  440  and NFETs  445 ,  450  and  455 . The A signal (the signal to be fenced to zero) is coupled to the gates of PFET  430  and NFET  445 . The PS SYNC signal (or PS signal in the second embodiment of the present invention) is coupled to the gates of NFET  450  and PFET  435 . The sources of PFETS  430 ,  435  and  440  are coupled to AVDD. The drains of NFETs  450  and  455  are coupled to GND. The source of NFET  445  is coupled to the drain of NFET  450 . The drains of PFET  435  and NFET  445  are coupled together and to the gates of PFET  440  and NFET  455 . The drains of PFET  440  and NFET  455  are coupled together and output the FA signal (the fenced A signal). 
     In FIG. 6, force to logical one circuit  355  is comprised of PFETs  460 ,  465 ,  470  and  475  and NFETs  480 ,  485 ,  490  and  495 . The PS SYNC signal (or PS signal in the second embodiment of the present invention) is coupled to the gates of PFET  460  and NFET  480 . The B signal (the signal to be fenced to one) is coupled to the gates of PFET  465  and NFET  490 . The sources of PFETs  465  and  475  are coupled to AVDD. The sources of NFETs  480 ,  485 ,  490  and  495  are coupled to GND. The drains of PFET  460  and NFET  480  are coupled to the gates of NFET  485  and PFET  470 . The source of PFET  470  and the drain of PFET  465  are coupled together. The drains of NFETs  485  and  490  and the drain of PFET  470  are coupled together and to the gates of PFET  475  and NFET  495 . The drains of PFET  475  and NFET  495  are coupled together and to output the FB signal (the fenced B signal). 
     Since PS SYNC (or PS in the second embodiment of the present invention) is always at a logical one or logical zero state the PS SYNC signal can be used to fence inputs A and B to voltage island  260 . As VDD drops the A signal drops to an unknown state “X”. In FIG. 5, PFET  430  and NFET  445  could both be on or both off, however, when PS SYNC (or PS) is low, NFET  450  will be off and PFET  435  will be on, forcing the AF signal to a high state. In FIG. 6, when the B signal is in the “X” state, PFET  465  and NFET  490  could both be on or both off, however when PS SYNC (or PS) is low, NFET  485  will be on and PFET  470  will be off, forcing the BF signal to a high state. 
     It is appropriate to now discuss some signal timing in fencing circuit  200 . FIG. 7 is a timing diagram illustrating the timing between the VDD, POS and PS SYNC signals of the circuit illustrated in FIG. 2 according to the present invention. In FIG. 7, the POS signal transitions from high to low at the point VDD drops to the first predetermined fraction (80%) of its reference value and transitions from low to high at the point VDD rises to the second predetermined fraction (81%) of its reference value. The PS SYNC (or PS) signal transitions from high to low a time δ after POS transitions from high to low. Delay δ is caused by the delay through AND gates  220  and  235  and latches  310 ,  315  and  320 . PS SYNC (or PS) transitions from low to high a time TPS after POS transitions from low to high. Delay TPS is caused by counter  225 , latch  230  and 66 MHz synchronizing logic circuit  240 . 
     FIG. 8 is a timing diagram of the circuit of the circuit illustrated in FIG. 3 according to the first embodiment of the present invention. The timing diagram of FIG. 8 comprises three sections. Section  500  shows the POS, CLK66, CLK32, CA, CB, PS SYNC1, FCA, FCB, PS SYNC, F CLK and VDD signals when VDD is on and as VDD is turned off. Section  505  shows the POS, CLK66, CLK32, CA, CB, PS SYNC1, FCA, FCB, PS SYNC, F CLK and VDD signals when VDD is turned off. Section  510  shows the POS, CLK66, CLK32, CA, CB, PS SYNC1, FCA, FCB, PS SYNC, F CLK and VDD signals when VDD is on and as VDD is turned off. In FIG. 8, the dotted lines indicates indeterminate levels. In FIGS. 9,  10  and  11 , the horizontal scale of CLK66 is not the same as the scale of the other parameters. 
     FIG. 9 is an expanded view of section  500  of the timing diagram illustrated in FIG. 8 according to the first embodiment of the present invention. In FIG. 9 the dotted lines indicates indeterminate levels. In FIG. 9, 32CLK is always on. FCA is always low and FCB is always high. POS goes from high to low before the CLK66 is turned off as does PS SYNC1 and PS SYNC, though PS SYNC and PS SYNC1 go low at the same time but after POS. PS SYNC and PS SYNC1 edges are aligned with FCLK edges. FCLK turns off when PS SYNC turns off. 
     FIG. 10 is an expanded view of section  510  of the timing diagram illustrated in FIG. 8 according to the first embodiment of the present invention. In FIG. 10 the dotted lines indicates indeterminate levels. In FIG. 9, 32CLK is always on. FCA is always low and FCB is always high. POS goes from low to high after the CLK66 is turned on as does PS SYNC1 and PS SYNC, though PS SYNC and PS SYNC1 are delayed “C” clock cycles, where “C” is equal to the maximum count in counter 225, in the present example, 16 32CLK cycles. PS SYNC and PS SYNC1 edges are aligned with CLK66 and FCLK edges. FCLK turns off when PS SYNC turns off. 
     FIG. 11 is a flowchart illustrating the initial power up of AVDD according to the first embodiment of the present invention. By initial power up we mean the first time an alternative source of power (i.e. a battery, is hooked up to the circuit.) Initially, in step  515 , AVDD is off and VDD is at the device technology operating voltage. Next in step  520 , power is applied to AVDD and AVDD is allowed to reach the device technology before VDD is shutdown. In step  525 , with AVDD at the device technology operating voltage, POS is off and the 32 KHz oscillator is operational. In step  530 , latches  300  and  305  in 32 KHz synchronizing logic circuit  215  and latches  310 ,  315  and  320  in 66 MHz synchronizing logic circuit  240  are initialized to zero. Finally, in step  535 , PS SYNC goes to zero. 
     FIG. 12 is a flowchart illustrating power down of VDD according to the first embodiment of the present invention. In step  540 , before VDD is turned off, VDD is high, POS is high and PS SYNC1 is high. In step  545 , VDD falls to 80% of its reference voltage level and POS goes low. In step  550 , AND gate  220  turns off and PS COUNT goes to zero. In step  555 , POS is synchronized to the CLK32K clock domain by 32K synchronizing logic circuit  215 . Next, in step  560 , after “M” CLK32 cycles latches  360 ,  365 ,  370 , and  370  in counter  225  are set to zero count driving PS DLY to zero. Then, in step  565 , PS DLY PLUS goes to zero. In the present example, “M” is between about 1 and 2 CLK32 cycles. Step  570  is simultaneous with step  555 . In step  570 , 66 MHz synchronizing logic circuit  240  latches  310  and  315  synchronize PS COUNT to the CLK66 clock domain. Next, in step  575 , 66 MHz synchronizing logic circuit  240  latch  320  synchronize PS COUNT to the low phase of the CLK66 domain. Then, in step  580 , after “N” CLK66 cycles, AND gate  235  turns off, PS SYNC goes low and AND gate  325  of fencing logic circuit  245  is turned off when the phase of CLK66 is low. In the present example, “N” is between about 1.5 and 2.5 CLK66 cycles. 
     FIG. 13 is a flowchart illustrating the power up of VDD according to the first embodiment of the present invention. In step  585 , AVDD is on, POS is low, PS SYNC is low before power is applied to VDD. In step  590 , when VDD rises to 81% of its reference value POS goes high. In step,  595  latches  310 ,  315  and  320  of 32 KHz synchronizing logic circuit  215  synchronize POS to the CLK32 clock domain. In step  600 , PS SYNC goes to 1 and counter  225  starts incrementing. In step  605 , counter  225  increments until a maximum count is reached (in this example 16) and the count stays at maximum until POS SYNC goes low. In step  610 , after one CLK32 cycle, PS DLY PLUS goes high. Step  615  occurs simultaneously with step  595  and before step  610 . In step  615 , the output of AND gate  220  (PS COUNT) is held low by the output of latch  230  (PS DLY PLUS) being low. Then, in step  620 , PS COUNT goes high. In step  625 , latches  310  and  315  of 66 MHz synchronizing logic circuit  240  synchronize PS COUNT to the CLK66 clock domain. In step  630 , latch  320  of 66 MHz synchronizing logic circuit  240  synchronizes PS COUNT to the low phase of the CLK66 domain. Finally, in step  635 , after “N” CLK66 cycles, AND gate  235  turns on, PS SYNC goes high and AND gate  325  of fencing logic circuit  245  is turned on when the phase of CLK66 is low. In the present example, “N” is between about 1.5 and 2.5 CLK66 cycles. 
     FIG. 14 is a schematic diagram of fencing circuit  640  for fencing signals to a voltage island according to a second embodiment of the present invention. In FIG. 14, a 32 KHz synchronizing logic circuit  645  comprises a latches  650  and  655 , a fencing logic circuit  660  comprises force to logical zero circuit  350 , force to logical one circuit  355 , OR gates  660  and  665 ,an AND gate  670  and an inverter  672  , a clock logic circuit  675  comprises OR gates  680  and  695 , an AND gate  690  and inverters  695  and  700 , and a counter  702  comprises AND gates  705  and  710 , latches  715  and  725  and a counting circuit  720 . Fencing logic  660  is located on a voltage island  702 . 
     In 32 KHz synchronizing logic circuit  645  the output of latch  650  is coupled to a data input of latch  655 . The output of voltage detector  205  (POS) is coupled to a data input of latch  650  and first inputs of AND gates  705  and  710 . The output of latch  655  (POS SYNC) is coupled to a second input of AND gate  705  and a data input of a latch  715 . The output of latch  715  (PS COUNT START) is coupled to a first input of counting circuit  720 . The output of counting circuit  720  (PS COUNT DONE) is coupled to a data input of latch  725  and a first input of OR gate  680  and the input of inverter  700 . The output of AND gate  705  (NRESET) is coupled to an inverting input of latch  715 , a second input of counter  720 , an inverting input of latch  725  and a first input of AND gate  690 . The output of latch  725  is coupled to a second input of AND gate  710 . Node  255  (AVDD) is coupled to 32K oscillator  280  and first inputs of force to logical zero circuit  350  and force to logical one circuit  355 . The output of 32 KHz clock  210  (CLK32) is coupled to a second input of OR gate  680  and a first input of OR gate  685 . The output of inverter  700  is coupled to a second input of AND gate  690 . The output of AND gate  690  is coupled to the input of inverter  695 . The output of inverter  695  is coupled to a second input of OR gate  685 . The output of AND gate  680  (CLK32 CG) is coupled to the clock inputs of latches  650  and  655 . The output of OR gate  685  (CLK32R CG) is coupled to the clock inputs of latches  715  and  725  and a third input of counter  720 . The output of AND gate  710 , a delayed standby clock synchronized power sense signal (PS), is coupled to second inputs of force to logical zero circuit  350  and force to logical one circuit  355  and a first input of OR gate  660 . An A signal is coupled to a third input of force to logical zero circuit  350  and a B signal is coupled to a third input of force to logical one circuit  355 . The output of force to logical zero circuit  350  is signal FA and the output of force to logical one circuit  355  is signal FB. PS TEST is coupled to a second input of OR gate  660 . A TA signal is coupled to a first input of AND gate  670 . A TB signal is coupled to a first input of OR gate  665 . The output of OR gate  670  is coupled to a second input of AND gate  670  and the input of inverter  672 . The output of inverter  672  is coupled to a second input of AND gate  665 . The output of AND gate  670  is signal FTA and the output of OR gate  665  is signal FTB. Signals FTA and FTB as signal FTS are coupled to latches  650 ,  655 ,  715 ,  725  and counter  720 . 
     When voltage detector  205  senses VDD dropping below 80% of its reference value POS goes low ultimately causing the output of AND gate  710  (PS) to go low while all fenced devices are still in there operating states. PS remains low as VDD continues to drop to zero and holds low when VDD is zero. 
     FIG. 15 a schematic diagram of the counter  720  of the circuit illustrated in FIG. 14 according to the second embodiment of the present invention. Counter  720  comprises latches  740 ,  745 ,  750 ,  755 , multiplexer  760 , AND gate  765  and adder  770 . PS COUNT is coupled to multiplexer  760 , NRESET is coupled to the inverting input of latches  740 ,  745 ,  750  and  755  and CLK32R CG is coupled to first clock inputs of latches  740 ,  745 ,  750  and  755 . FTS is coupled to second clock inputs of latches  740 ,  745 ,  750  and  755 . The output of AND gate  765  is PS COUNT DONE. The output of latch  740  (COUNT 0) is coupled to a first input of AND gate  765  and a first input of adder  770 . The output of latch  745  (COUNT 1) is coupled to a second input of AND gate  765  and a second input of adder  770 . The output of latch  750  (COUNT 2) is coupled to a third input of AND gate  765  and a third input of adder  770 . The output of latch  755  (COUNT 3) is coupled to a fourth input of AND gate  765  and a fourth input of adder  770 . Outputs INC 0, INC 1, INC 2, and INC 3 are coupled to multiplexer  760 . A first output of multiplexer  760  (PS INC 0) is coupled to the data in of latch  740 . A second output of multiplexer  760  (PS INC 1) is coupled to the data in of latch  745 . A third output of multiplexer  760  (PS INC 2) is coupled to the data in of latch  750 . A fourth output of multiplexer  760  (PS INC 3) is coupled to the data in of latch  755 . 
     FIG. 16 is a plot of the VDD signal vs. time according to the second embodiment of the present invention. TSR is defined by the difference in the time VDD reaches the minimum voltage required by the device technology VMIN and the time VDD reaches the first predetermined fraction (80%) of its reference value. In the present example of 66 MHz and 32 KHz clocks, TRS must be greater than or equal to 60 microseconds in order to be sure the latches  715 ,  725 ,  740 ,  745 ,  750  and  755  reset and are not in a metastable state when POS switches at the same time CLK32 switches. 
     FIG. 17 is a flowchart illustrating power down of VDD according to the second embodiment of the present invention. In step  775  VDD, POS and PS are high. In step  780 , when VDD drops to less than the first predetermined fraction (80%) of reference voltage POS goes low. In step  785 , PS, NRESET go low and latches  715  and  725  as well as latches  740 ,  745 ,  750  and  755  in counter  720  reset. In step  790 , PS and VDD then go low. 
     FIG. 18 is a flowchart illustrating the power up of VDD according to the second embodiment of the present invention. In step  795 , VDD, POS and PS are low. In step  800 , when VDD reaches VMIN, latches  715 ,  725 ,  740 ,  745 ,  750  and  755  are reset to a low state. Steps  805  and  810  occur simultaneously. In step  805 , latches  650  and  655  synchronize POS to the CLK32 domain. In step  810  VDD reaches the second predetermined fraction (81%)of reference voltage. In step  815 , PS SYNC goes high. In step  820  PS COUNT START goes high and counter  820  is enabled to increment. In step  825 , latch  725  is enabled, PS ENABLE goes high, clock logic circuit  675  gates clocking of latches  650 ,  655 ,  715 ,  725 ,  740 ,  745 ,  750  and  755 , counter  720  stops incrementing and PS hoes high. 
     It should be understood that, for the first embodiment of the present invention, voltage detector  205 , 32K Clock  210 , power supply  247  and 66 MHz synchronizing logic circuit  240  may feed multiple voltage islands  260 , each having its own copy of 32 Kz synchronizing logic circuit  240 , counter  225 , combinational logic  237  and fencing logic circuit  245 . Optionally, a single 32 Kz synchronizing logic circuit  240  may feed multiple voltage islands. With the addition of one or more low frequency clocks several voltage islands running at different frequencies are possible. For the second embodiment of the present invention, voltage detector  205 , 32K Clock  210 , power supply  247 , clock logic circuit  675 , AND gates  705  and  710 , latches  715  and  725  and counter  720  may feed multiple voltage islands  702  each having its own copy of fencing logic circuit  660 . Optionally, a single 32 Kz synchronizing logic circuit  645  may feed multiple voltage islands. 
     The description of the embodiments of the present invention is given above for the understanding of the present invention. It will be understood that the invention is not to the particular embodiments described herein, but is capable of various modifications, rearrangements and substitutions, as for example, different values may be used for any of the clock frequencies, as will now become apparent to those skilled in the art without departing from the scope of the invention. Therefore it is intended that the following claims cover all such modifications and changes as fall within the true spirit and scope of the invention.

Technology Classification (CPC): 8