Patent Abstract:
Method and apparatus for implementing ultrasonic systems that maximize efficiency by dynamically detecting and maintaining peak operational resonance frequency. In one embodiment, the invention dynamically sweeps the output frequency range to locate the peak load current. The resonance frequency corresponding to the peak load current is used as a reference frequency in a control loop. The control loop includes a voltage-controlled oscillator (VCO) that is controlled by a loop controller and operates to lock onto the dynamically sensed reference frequency. In response to the VCO output, a pulse-width modulator (PWM) circuit drives a pair of switches that adjust transducer current to maintain the circuit locked on the resonance frequency at a substantially constant current.

Full Description:
BACKGROUND OF THE INVENTION 
     The present invention relates in general to ultrasonic systems, and in particular to methods and circuitry for driving an ultrasonic transducer. 
     Ultrasound technology is utilized in a variety of applications from machining and cleaning of jewelry crystals to performing surgical operations involving for example clearing obstructed blood vessels, to disrupting or lysing cells in order to release the inracellular contents (e.g., nucleic acid). The basic concept of ultrasonic systems involves the conversion of high frequency electric energy into ultrasonic frequency mechanical vibrations using transducer elements. Such systems typically include a driver circuit that generates electrical signals which excite a piezoelectric transducer assembly. A transmission element such as a probe connects to the transducer assembly and is used to deliver mechanical energy to the target. 
     For a given user-defined parameter (e.g., amplitude level) there is a resonance frequency at which the driver circuit operates most efficiently. The driver circuit is thus designed to operate at resonance frequency for a particular application. In many applications, however, due to changes in the environmental conditions the optimal resonance frequency drifts as the mechanical energy is being delivered. Such varying environmental conditions may include, for example, changes in temperature or the consistency of the target itself. The challenge, therefore, is to design an ultrasonic system that adapts to such environmental variations such that the driver circuit operates at its optimal resonance frequency at all times. 
     BRIEF SUMMARY OF THE INVENTION 
     The present invention provides methods and apparatus for implementing an ultrasonic system that dynamically detects and maintains peak operational resonance frequency. In one embodiment, the invention dynamically sweeps the output frequency range to locate the peak load current. The resonance frequency corresponding to the peak load current is used as a reference frequency in a control loop such as a phase-locked loop (PLL). The control loop includes a voltage-controlled oscillator (VCO) that is controlled by a loop controller such as a microprocessor and operates to lock onto the dynamically sensed reference frequency. In response to the VCO output, a pulse-width modulator (PWM) circuit drives a pair of switches that adjust transducer current to maintain the circuit locked on the resonance frequency at a substantially constant current. By combining the frequency sweeping feature that locates the peak load current and the resonance frequency, with the microprocessor controlled pulse width modulated current switches, the invention provides for an ultrasonic system that maintains a substantially constant displacement of the transmission element with maximum efficiency. The invention further provides an algorithm that allows the user to specify parameters such as amplitude level of the driver, and then performs a multi-step frequency sweep to drive the transducer in one of several modes including constant current drive, constant voltage drive and constant power drive. In various specific embodiments, the invention provides additional features such as optional circuit alarm and VCO linearity compensation. 
     Accordingly, in one embodiment, the present invention provides an ultrasonic system including: a transducer coupled to a secondary of a transformer; and a control loop coupled between the transducer and a primary of the transformer, wherein the control loop includes a current sense circuit coupled to the transformer and configured to detect load current; a loop controller coupled to the current sense circuit and configured to dynamically set a loop reference frequency in response to the sensed load current; a voltage-controlled oscillator (VCO) coupled to the controller and configured to generate an output signal oscillating at the reference frequency; and a pulse-width modulator coupled to the VCO and configured to control an amount of current in the primary of the transformer. 
     In another embodiment, the present invention provides a driver circuit for an ultrasonic transducer, wherein the driver circuit includes: a current sense circuit coupled to detect a transducer load current; a controller coupled to the current sense circuit and configured to set a reference frequency corresponding to peak resonance frequency; a voltage-controlled oscillator (VCO) coupled to the controller and configured to generate an output signal oscillating at the reference frequency; and a pulse width modulator coupled to the VCO and configured to modulate an output current of the driver circuit. The pulse width modulator includes a first switch and a second switch whose operation is controlled by pulse width modulated signals generated in response to the VCO output signal. 
     In yet another embodiment, the present invention provides a method for driving an ultrasonic transducer, wherein the method includes (a) sweeping a frequency range of the output to locate a peak load current; (b) defining a reference frequency as the frequency corresponding to the peak current; (c) adjusting an oscillation frequency of an oscillator to the reference frequency; (d) controlling output transistor switches by pulse width modulated signals generated in response to the oscillator output to adjust transducer current; and (e) periodically repeating steps (a) through (d) to dynamically adjust the reference frequency that controls the transducer current. 
     The following detailed description and the accompanying drawings provide a better understanding of the nature and advantages of the present invention. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is a simplified block diagram of a driver circuit for an ultrasonic system according to one embodiment of the invention; 
     FIG. 2 is a flow diagram illustrating the method of operating an ultrasonic system according to one embodiment of the invention; 
     FIG. 3 shows waveforms that illustrate the operation of the pulse-width modulated signals; 
     FIG. 4 is a flow diagram illustrating an exemplary algorithm used by the ultrasonic driver of the present invention to detect the peak load current; 
     FIG. 5 shows an exemplary implementation for a current sense circuit used in the driver circuit of the present invention; 
     FIG. 6 shows an exemplary implementation for a voltage-controlled oscillator used in the driver circuit of the present invention; 
     FIG. 7 shows an exemplary implementation for pulse-width modulated switches that control the amount of current being delivered to the transducer according to the present invention; and 
     FIG. 8 is a cross sectional view of an apparatus including an ultrasonic transducer according to the present invention that is used for disrupting cells or viruses. 
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     Referring to FIG. 1, there is shown a simplified block diagram of a driver circuit  100  for an ultrasonic transducer according to one embodiment of the invention. Driver circuit  100  includes a current sense block  102  that is magnetically coupled to the load. Current sense block  102  detects the load current and generates an analog signal representative of the amplitude of the load current. The analog current sense signal is converted to a digital signal by an analog-to-digital converter or ADC  104 . The output of ADC  104  is supplied to a controller or microprocessor  106 . Microprocessor  106  uses the digital signal to determine the peak resonance frequency and sends a digital signal corresponding to the resonance frequency to a digital-to-analog converter DAC  108 . DAC  108  converts this signal into an analog voltage signal that controls the oscillation frequency of a voltage-controlled oscillator (VCO)  110 . The output of VCO  110  connects to a pulse-width modulator (PWM) control circuit  112  that generates pulse signals PWM 1  and PWM 2  at the desired frequency. Signals PWM 1  and PWM 2  drive switches S 1  and S 2  that in turn control the amount of current being delivered to the transducer. 
     The operation of the driver circuit according to one exemplary embodiment of the invention will be described in connection with the broad and simplified flow diagram of FIG.  2 . In a typical application, the user specifies an amplitude level and a time duration for the operation of the ultrasonic device. Software stored in microprocessor  106  translates the amplitude level into a desired current level I(h) for the transduce. Referring to FIG. 2, at step  200  the microprocessor determines the desired transducer current level I(h) based on user specified amplitude level. This is followed by a frequency profile sweep (step  202 ) to locate the peak load current (step  204 ). Current sense block  102  detects the peak current and supplies this information to microprocessor  106  via ADC  104 . Microprocessor  106  uses this information to determine the peak resonance frequency. This resonance frequency is used as the control loop reference frequency (step  206 ). Microprocessor  106  adjusts the frequency of operation of VCO  110  via DAC  108  such that it locks to the reference frequency (step  208 ). PWM control circuit  112  then receives the output of VCO  110  and generates signals PWM 1  and PWM 2  (step  210 ). PWM control circuit  112  divides the VCO output signal into two alternating non-overlapping signals by taking one signal from the rising edge of the VCO output and a second signal from the falling edge of the VCO output. 
     FIG. 3 shows signal waveforms for PWM 1  and PWM 2  that are generated from a VCO output signal having an exemplary frequency of 36 kHz. Signals PWM 1  and PWM 2  control switches S 1  and S 2  that in turn control the amount of current being pulled from transformer  114  which has a voltage input Vin at its center tap. The secondary of transformer  114  drives the resonating crystal  116 . The transducer current I(h) is periodically detected (step  212 ) and compared against the target value. If the measured current drifts outside a preset range around the target value, the PWM signals are adjusted by repeating steps  202  to  210 . Thus, the system remains locked at resonance frequency on the specified current and deviates only within the specified range. 
     The frequency profile sweep, according to one embodiment of the invention, occurs in multiple steps with increasing granularity to locate the peak current with a high degree of precision. The flow diagram of FIG. 4 depicts an alternative embodiment of the present invention which employs an exemplary multi-step sweeping technique. According to this alternative embodiment, after determining the desired output current (step  400 ), the process includes an initial broad sweep (step  402 ) of the output frequency profile involving, for example, ten 100 Hz frequency steps to locate the approximate position f 1  of the peak current. This is followed by a second medium sweep (step  404 ) involving, for example, ten 10 Hz frequency steps centered around f 1 , five steps to the left and five steps to the right. A more accurate location f 2  for the peak current is obtained by the second sweep. A final narrow sweep is then performed (step  406 ) using, for example, ten 1 Hz steps centered around f 2 . The final sweep yields a highly precise location f 3  for the peak current. The resonance frequency f 3  is then used to set the driver frequency (step  408 ), after which the transducer current I(h) is measured (step  410 ). In this embodiment, the final narrow sweep (step  406 ) is repeated periodically as long as I(h) remains within the target range. When I(h) falls outside of the target range, the PWM signals are adjusted based on the differential (step  412 ), and a new frequency sweep (step  414 ) is performed with the adjusted PWM signals before the loop is repeated. The new sweep at step  414  can be performed in, e.g., 20 steps at 20 Hz centered around f 3  to determine a new and more accurate resonance frequency. Note that the final narrow sweep (step  406 ) can be repeated as many times as necessary to keep the circuit locked on to the resonance frequency at the desired target current at all time. For example, in one embodiment, the final sweep is repeated every few milliseconds. 
     In a specific embodiment, the present invention provides an algorithm that enables the user to drive the circuit in three different modes. The first mode is the constant current drive described above. In this mode, once the circuit locks onto the resonance frequency, a software routine checks the digital current reading to determine if it matches the user&#39;s specifications within a preset range. If the current reading falls outside the preset range, the controller initiates another frequency sweep of, for example, 20 steps at 20 Hz per step, and adjusts the PWM signals accordingly. It will then check the digital current reading once again to determine if it matches the user&#39;s specification. In this manner, the system maintains lock on the specified current and deviates only within a narrow preset range. Using the process described above in connection with FIG. 4, both the lock on resonance frequency and the lock on constant current level can be simultaneously and continuously monitored. 
     A second mode of operation allows for a constant voltage drive. In this mode, the circuit drives the transducer at a fixed voltage set by a constant pulse width modulation. The microprocessor sets the PWM to the user&#39;s specification and performs the multi-step frequency profile sweep to lock on to the resonance frequency. The constant voltage drive mode fixes the PWM to a given value and therefore allows the current to drift up or down. 
     The third mode of operation is constant power driver. The voltage applied to the load is a function of PWM that is controlled by the microprocessor. In this mode, the microprocessor adjusts the current such that the product of voltage across the load and the current is kept constant. 
     A specific implementation of the ultrasonic driver circuit according to an exemplary embodiment of the invention will be described in connection with FIGS. 5-7. Referring to FIG. 5, there is shown one embodiment of the current sense block  102 . A current transformer  502  magnetically couples the current sense circuit to the transducer (not shown in FIG.  4 ). A sense resistor R 166  connects across the terminals of current transformer  502  such that the signal developing across resistor R 166  represents the magnitude of the transducer current I(h). This signal goes through a filter  504  and then a DC rectifier  506 . Filter  504  is a low pass filter that is designed to amplify the signal and remove additional harmonics. In the exemplary embodiment shown filter  504  is implemented by a fourth order active low pass (butterworth) filter. Rectifier  506  is a full-wave rectifier that converts the signal into a DC value HORN_CUR that is then sent to the analog-to-digital converter (ADC  104  in FIG.  1 ). An alarm circuit  508  can be optionally added to protect the circuit against accidental power surge or other related failures. Alarm circuit  508  includes a comparator  510  that compares the transducer current HORN_CUR to a preset threshold or reference signal REF. If the transducer current HORN_CUR exceeds the threshold value, alarm circuit  508  generates a fault_alarm signal that is supplied to the microprocessor. The microprocessor in turn shots off the PWM circuitry to prevent any damage to the circuit board or the resonating crystal. 
     FIG. 6 is a partial schematic of an exemplary implementation for the voltage-controlled oscillator of the present invention. There a number of different known implementations for a VCO. In this embodiment, a 74HCT4046 chip  600  is used which has a frequency range determined by a voltage input at VCOIN from 0 to 5V. VCO chip  600 , however, has a limited linear frequency range of e.g., 2.7V. To compensate for this problem, this specific embodiment of the invention includes a linearity compensation circuit  602  that receives the signal FREQ from the microprocessor and operates to extend the linear range of the VCO to almost the entire 5V range. Variable resistors R 151  and R 152  are used tune the lower frequency range and the overall frequency range, respectively. The output of VCO  600 , signal VCOUT is applied to PWM control circuit ( 112  in FIG. 1) to generate signals PWM 1  and PWM 2 . In one embodiment, PWM control circuit  112  is implemented using a programmable logic device. 
     FIG. 7 provides a more detailed circuit schematic of an illustrative implementation of the PWM switches that drive the transducer. In this exemplary implementation, each of the signals PWM 1  and PWM 2  are first applied to a driver amplifier  702  and  704 , respectively. Switches S 1  and S 2  are implemented by n-type metal-oxide-semiconductor filed effect transistor (MOSFETs) where drivers  702  and  704  drive the gate terminals of S 1  and S 2 , respectively. MOSFET S 1  has one current-conducting (drain) terminal connected to a first node  706  of the primary of a dual transformer  712 , and its second current-conducting (source) terminal connected to ground. MOSFET S 2  has one current-conducting (drain) terminal connected to a second node  706  of the primary of dual transformer  712 , and its second current-conducting (source) terminal connected to ground. As thus constructed, the circuit results in a class D push-pull power amplifier. It is to be understood, however, that other amplifier topologies such as class C and E can also be employed for high efficiency. The center tap (node  710 ) of the primary of dual transformer  712  is connected to a voltage input having a voltage of, e.g., 24V. The secondary of transformer  712  connects to the transducer. The voltage input of the transformer center tap can vary depending on the application. To improve the performance of MOSFETs S 1  and S 2  as switches, transient voltage suppressors and Schottky diodes are added to each one. 
     The advantages of the ultrasonic system of the present invention make it particularly well suited for certain applications. For example, in the fields of molecular biology and biomedical diagnostics, it is often necessary to extract nucleic acid from cells or viruses. Once released from the cells, the nucleic acid may be used for genetic analysis such as sequencing, pathogen identification and quantification, and the like. The extraction of nucleic acids from cells or viruses is generally performed by physical or chemical methods. While known methods for disrupting cells or viruses have had some measure of success, most suffer from certain drawbacks and disadvantages including those involving ultrasonic agitation. Typical problems with existing ultrasonic lysis of cells include non-uniform distribution of ultrasonic energy, slow lysing process, physical damage over time to sample container, non-portability of the system, etc. 
     In another embodiment, the present invention employs the ultrasonic system of the present invention to provide an improved apparatus and method for disrupting cells or viruses to release the nucleic acid therefrom. The invention, according to this embodiment, provides for rapid, non-invasive lysis of cells or viruses held in a container by applying a vibrating surface of a transducer device to a wall of the container without melting, cracking, or otherwise damaging the wall of the container. FIG. 8 shows a cross sectional view of an apparatus including an ultrasonic transducer  36  and horn  38  that is used for lysing cells or viruses. The apparatus includes a container  18  having a chamber  40  for holding a liquid containing the cells or viruses. The chamber  40  has a wall  46  for contacting the vibrating tip  50  of the horn  38 . The wall  46  thus provides an interface between the transducer/horn assembly and the contents of the chamber  40 . In the exemplary embodiment shown in FIG. 8, the wall  46  is dome-shaped and convex. In alternative embodiments, the interface wall  46  may have other forms, such as a flat wall, a wall with stiffening ribs, or a wall comprising a flexible plastic film. The wall  46  is preferably sufficiently elastic to deflect in response to vibratory movements of the horn tip  50 . The transducer  36  is driven by a driver circuit  34  as previously described with reference to FIG. 1 to operate at the optimum frequency. The vibration of the transducer/horn assembly deflects the wall  46  to generate pressure waves or pressure pulses in the chamber  40  to effect lysis of the cells or viruses in the chamber. Optionally, the chamber  40  may contain beads  66  that are agitated by the sonication of the chamber  40 . The beads move violently in response to the pressure waves or pressure pulses in the chamber  40  to rupture the cells or viruses. The chamber  40  may also optionally include a filter  48  for trapping cellular debris as the lysate is forced to flow out the outlet port  44  of the container  18 . The transducer/horn assembly may be coupled to the container  18  using any suitable holding mechanism, and in particularly preferred embodiments, the transducer/horn assembly is biased against the interface wall  46  using an elastic body (e.g., one or more springs or compressed air). 
     Many modifications to the lysis apparatus shown in FIG. 8 are possible. For example, the ultrasonic transducer may be directly coupled to the chamber wall  46 , so that the horn  38  is eliminated. In one alternative embodiment, the transducer comprises piezoelectric material (e.g., a piezoelectric stack made of layers of piezoelectric material) that is directly coupled to the chamber wall  46 . The piezoelectric material is driven by the driver circuit  34  causing the piezoelectric material to vibrate at a suitable frequency and amplitude to sonicate the chamber  40  and lyse the cells or viruses therein. In an alternative embodiment, the piezoelectric transducer includes a top layer of material (e.g., sheet metal or mylar) that is placed in contact with the external surface of the chamber wall  46 . The top layer of material thus couples the piezoelectric material to the wall  46  and provides the vibrating surface for deflecting the wall. A more detailed description of the various systems and methods for lysing of cells or viruses according to the ultrasonic lysis embodiments of the present invention can be found in commonly assigned patent applications PCT/US00/14740 filed May 30, 2000 and published as WO 00/73413 Dec. 7, 2000, and U.S. Ser. No. 09/972,221 filed Oct. 4, 2001 entitled “Apparatus and Method for Rapid Disruption of Cells or Viruses”, both of which patent applications are hereby incorporated by reference in their entirety. 
     It is to be understood that the specific embodiments described above are for illustrative purposes only, and that various modifications, alternative implementations and equivalents are possible. For example, the various functional blocks shown in the block diagram of FIG. 1 could be integrated in different combinations. Some of the functionality described could be implemented in software or hardware, or a modified combination thereof. Furthermore, specific numerical values given for frequencies of operation and voltage levels are for illustrative purposes only, and different applications may require different frequency ranges and current and voltage levels. Similarly, many different variations and equivalents are possible for the specific circuit implementations shown in FIGS. 5-7. For example, switches S 1  and S 2  may be implemented by different types of transistors including for example, p-type MOSFETs, bipolar junction transistors, and the like. The scope of the invention should therefore not be limited to the embodiments described above, and should instead be determined by the following claims and their full breadth of equivalents.

Technology Classification (CPC): 1