Patent Abstract:
A method for sensing the current in a high-electron-mobility transistor (HEMT) that compensates for changes in a drain-to-source resistance of the HEMT. The method includes receiving a sense voltage representative of the current in the HEMT, receiving a compensation signal representative of a drain-to-source voltage of the HEMT, and outputting as a compensated sense voltage a linear combination of the sense voltage and the compensation signal.

Full Description:
BACKGROUND 
     1. Field of Disclosure 
     This application relates generally to current sense transistors and, more specifically, to techniques to compensate for variations in the current sense ratio between a current sensing transistor and a main transistor. 
     2. Description of the Related Art 
     Current sense transistors have been used for many years in integrated circuit applications where accurate current sensing can provide information for both control and over-current protection. Sense transistors are typically constructed from a small part or section of a larger transistor that carries the main current of the device. For example, in a conventional metal oxide semiconductor field effect transistor (MOSFET) device, the sense transistor may comprise a small section of the channel region of the main power transistor. In operation, the sense transistor may sample a small fraction of the channel current of the power transistor, thereby providing an indication of the current in the main transistor. The sense transistor and main transistor device typically share a common drain and gate, but each has a separate source electrode. 
     Sense transistors are useful in many power delivery applications to provide current limit protection and accurate power delivery. In providing these functions, the sense transistor generally maintains a constant current sensing ratio (CSR) with respect to a main power transistor over a wide range of drain currents (100 mA to 10 amperes), temperatures (−25° C. to 125° C.), as well as fabrication process variations and mechanical stress/packaging variations. The ratio of drain current of the main power transistor to that of the sense transistor typically ranges between 20:1 to 800:1, or greater. 
     High electron mobility transistors (HEMTs) are attractive devices for achieving high performance in high power applications as they have high electron mobility and a wide band gap, and are capable of being processed with conventional equipment and methods not substantially different from those already developed for silicon and present generations of compound semiconductors. A particularly desirable material for building a HEMT is the wide-bandgap compound semiconductor known as gallium nitride (GaN). The GaN-based transistor is capable of maximizing electron mobility by forming a quantum well at the heterojunction interface between e.g., an aluminum gallium nitride (AlGaN) barrier layer and a GaN layer. GaN-based transistors have received much attention for high power applications since they have on-resistances that are typically one or more orders of magnitude less than those of silicon (Si)-based or gallium arsenide (GaAs)-based transistors and hence, are operable at higher temperatures with higher currents and can withstand high voltage applications. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       Non-limiting and non-exhaustive embodiments of the present invention are described with reference to the following figures, wherein like reference numerals refer to like parts throughout the various views unless otherwise specified. 
         FIG. 1A  is a schematic representation of cross-sectional view of a lateral-channel HEMT. 
         FIG. 1B  is a schematic representation of top-view of a HEMT device including two HEMTs coupled together. 
         FIG. 2A  is a circuit schematic of an example HEMT device that includes a main transistor and a sense transistor for sensing the drain current of the main transistor. 
         FIG. 2B  is a circuit schematic that illustrates an equivalent representation of the HEMT device of  FIG. 2A . 
         FIG. 2C  is a circuit schematic of a HEMT device including a main transistor and two sense transistors. 
         FIG. 3  shows example waveforms that correspond to a sense voltage representative of the drain current of the main transistor of the HEMT devices of  FIG. 2A-2C , a compensation signal, and a compensated sense voltage. 
         FIG. 4A  is a circuit schematic illustrating one example implementation of a compensation circuit that outputs a compensated sense voltage. 
         FIG. 4B  is a circuit schematic illustrating another example implementation of a compensation circuit that outputs a compensated sense voltage. 
         FIG. 4C  is a circuit schematic illustrating yet another example implementation of a compensation circuit that outputs a compensated sense voltage. 
         FIG. 5  shows example normalized curves that correspond to a ratio of the drain current of the main transistor of the HEMT device in  FIG. 2C  to a sense current and a ratio of the drain current of the main transistor of the HEMT device in  FIG. 2C  to a compensated sense current. 
         FIG. 6  is a circuit schematic of another example HEMT device including a main transistor and two sense transistors. 
     
    
    
     DETAILED DESCRIPTION 
     Among the challenges that arise in the design of a sense transistor for use in a power integrated circuit (IC) with a GaN-based power transistor is the variation of the drain to source resistance of the power transistor with respect to its drain to source voltage. As a result, for a fixed drain current of the power transistor, the current sampled by the sense transistor varies as the drain to source voltage of the power transistor varies. This causes the current sense ratio to deviate from the desired constant value. 
       FIG. 1A  is a schematic representation of cross-sectional view of an example lateral-channel HEMT  100 . HEMT  100  includes a substrate layer  110 , a first semiconductor layer  120 , and a second semiconductor layer  130 . First semiconductor layer  120  and second semiconductor layer  130  contact one another to form a heterojunction. Due to the material properties of semiconductor layers  120  and  130 , a two dimensional electron gas arises at the heterojunction. HEMT  100  also includes a source electrode  140 , a drain electrode  160 , and a gate electrode  150 . The selective biasing of gate electrode  150  regulates the conductivity between source electrode  140  and drain electrode  160 . 
     In the illustrated implementation, source electrode  140  and drain electrode  160  both rest directly on an upper surface of second semiconductor layer  130  to make electrical contact therewith. This is not necessarily the case. For example, in some implementations, source electrode  140  and/or drain electrode  160  penetrate into second semiconductor layer  130 . In some implementations, this penetration is deep enough that source electrode  140  and/or drain electrode  160  contact or even pass through the heterojunction. As another example, in some implementations, one or more interstitial glue, metal, or other conductive materials are disposed between source electrode  140  and/or drain electrode  160  and one or both of semiconductor layers  120 ,  130 . 
     In the illustrated implementation, gate electrode  150  is electrically insulated from second semiconductor layer  130  by a single electrically-insulating layer  170  having a uniform thickness. This is not necessarily the case. For example, in other implementations, a multi-layer can be used to insulate gate electrode  150  from second semiconductor layer  130 . As another example, a single or multi-layer having a non-uniform thickness can be used to insulate gate electrode  150  from second semiconductor layer  130 . 
     The various features of lateral-channel HEMT  100  can be made from a variety of different materials, including Group III compound semiconductors. For example, first semiconductor layer  120  can be one of gallium nitride (GaN), indium nitride (InN), aluminum nitride (AlN), aluminum gallium nitride, (AlGaN), indium gallium nitride (InGaN), and indium gallium aluminum nitride (InGaAlN). In some implementations, first semiconductor layer  120  can also include compound semiconductors containing arsenic such as one or more of, e.g., gallium arsenide (GaAs), indium arsenide (InAs), aluminum arsenide (AlAs), indium gallium arsenide (InGaAs), aluminum gallium arsenide (AlGaAs), and indium aluminum gallium arsenide (InAlGaAs). Second semiconductor layer  130  can be, e.g., AlGaN, GaN, InN, InGaN, or AlInGaN. Second semiconductor layer  130  can also include compound semiconductors containing arsenic such as one or more of GaAs, InAs, AlAs, InGaAs, AlGaAs, or InAlGaAs. The compositions of first and second semiconductor layers  120 ,  130 —which also can be referred to as active layers—are tailored such that a two-dimensional electron gas forms at the heterojunction. For example, in some implementations, the compositions of first and second semiconductor layers  120 ,  130  can be tailored such that a sheet carrier density of between 10 11  to 10 14  cm −2  arises at the heterojunction. In some implementations, a sheet carrier density of between 5×10 12  to 5×10 13  cm −2  or between 8×10 12  to 1.2×10 13  cm −2  arises at the heterojunction. First and second semiconductor layers  120 ,  130  can be formed above substrate layer  110  which can be, e.g., GaN, GaAs, silicon carbide (SiC), sapphire (Al 2 O 3 ), or silicon. First semiconductor layer  120  can be in direct contact with such a substrate layer, or one or more intervening layers can be present. 
     Source electrode  140 , drain electrode  160 , and gate electrode  150  can be made from various electrical conductors including, e.g., metals such as aluminum (Al), nickel (Ni), titanium (Ti), titanium tungsten (TiW), titanium nitride (TiN), titanium gold (TiAu), titanium aluminum molybdenum gold (TiAlMoAu), titanium aluminum nickel gold (TiAlNiAu), titanium aluminum platinum gold (TiAlPtAu), or the like. Insulating layer  170  can be made from various dielectrics suitable for forming a gate insulator including, e.g., (Al 2 O 3 ), zirconium dioxide (ZrO 2 ), aluminum nitride (AlN), hafnium oxide (HfO 2 ), silicon dioxide (SiO 2 ), silicon nitride (Si 3 N 4 ), aluminum silicon nitride (AlSiN), or other suitable gate dielectric materials. Insulating layer  170  can also be referred to as a passivation layer in that layer  170  hinders or prevents the formation and/or charging of surface states in the underlying second semiconductor layer  130 . 
       FIG. 1B  is a schematic representation of a top-view of an example HEMT device including two HEMTs coupled together. As shown, source electrodes have metal pads that are coupled to a source metal bus  192  used to couple source electrodes of HEMTs  180  and  190  together. Similarly, gate electrodes have metals pads that are coupled to a gate metal bus  194  used to couple gate electrodes of HEMTs  180  and  190  together and drain electrodes have metal pads that are coupled to a drain metal bus  196  used to coupled drain electrodes of HEMTs  180  and  190  together. As such, in this configuration, the illustrated HEMT device includes two HEMTs coupled in parallel. In one example, one of HEMTs  180  and  190  can be used as a sense transistor to sense the drain current of the other, which may be referred to as a main transistor. In another example, the HEMT device can include more than one sense transistor coupled to the main transistor in parallel in the same manner as explained above. The main transistor and the one or more sense transistors may be formed on a single die. In some examples, there can be a resistor coupled between the metal pad of the source electrode of each one of the sense transistors and source metal bus  192 . This resistor can be used to measure the current in the sense transistor(s). In the depicted example, for illustrative purposes only, the gate electrodes of HEMTs  180  and  190  are drawn to be smaller in one dimension than the source and drain electrodes. In other examples, gate electrodes can be approximately the same size as the source and/or drain electrodes. 
       FIG. 2A  is a circuit schematic that includes an example HEMT device having a main transistor and a sense transistor for sensing the drain current of the main transistor. As shown, a HEMT Q 1    202 , also referred to as main transistor  202 , is coupled across a current source  200  between a node A and a ground reference  210 . Ground reference  210  represents the lowest voltage or potential against which all voltages of the illustrated circuit are measured or referenced. HEMT Q 1    202  has a drain terminal coupled to the node A, a source terminal coupled to ground reference  210 , and a control terminal (gate) also coupled to ground reference  210 . In the example of  FIG. 2A , transistor  202  is a depletion mode transistor, being in a conducting state when the gate terminal is less than a threshold voltage above the source terminal. A depletion mode transistor is sometimes called a normally-on transistor. Therefore, transistor  202  is in a conducting state when the source terminal and the gate terminal are coupled to the same potential. In a typical application, the gate terminal may be coupled to a driver circuit that changes the voltage at the gate terminal to switch the transistor between a conducting state and a non-conducting state. In one example, HEMT Q 1    202  is a Group III compound semiconductor FET such as, for example, a GaN FET. It should be noted that, with appropriate modification, other transistor types such as, for example, a metal oxide semiconductor FET (MOSFET) or a junction FET (JFET) can also be used as the main transistor. 
     The HEMT device includes a HEMT sense transistor Q SEN    204  for sensing the drain current of the main transistor. Sense transistor  204  shares drain and control terminals with those of main transistor  202 . Source terminal of sense transistor  204  is coupled to ground reference  210  with a sense resistor R SEN    206 . Sense transistor  204  is also a depletion mode transistor; hence, sense transistor  204  is in a conducting state when the voltage at its gate terminal is less than a threshold voltage above its source terminal. 
     Current source  200  is coupled to provide a current I D  to the node A. The current I D  is approximately equal to the drain current of main transistor  202 . A relatively small fraction (e.g., one hundredth or less) of this current is drawn by sense transistor  204  as a sense current I SEN    208 . Therefore, sense current I SEN    208  is representative of the drain current of main transistor  202 . Since sense resistor R SEN    206  conducts the same current as sense transistor  204 , the voltage that develops across sense resistor R SEN    206 , which is referred to as a sense voltage V SEN    212 , is representative of sense current I SEN    208 . Hence, V SEN    212  sense voltage is also representative of the drain current of main transistor  202 . In operation, sense voltage V SEN    212  is less than the threshold voltage of sense transistor  204  so that sense transistor  204  is in the conducting state when main transistor  202  is conducting current. 
       FIG. 2B  is a schematic of an equivalent circuit of the circuit of  FIG. 2A  with HEMTs Q 1    202  and Q SEN    204  in the ON state. When conducting current, main transistor  202  presents a certain amount of resistance between its drain and source terminals (i.e., drain to source resistance). As such, main transistor  202  can be modeled as a resistor R FET    222  coupled between the node A and ground reference  210 . In this case, resistor R FET    222  is representative of the drain to source resistance of main transistor  202 . Similarly, sense transistor  204  can be modeled as a resistor  224  coupled between sense resistor R SEN    206  and the node A. Resistor  224  represents the drain to source resistance presented by sense transistor  204  when sense transistor  204  is in a saturated conductive state. Resistor  224  may have a resistance that is several times (e.g., 100 times) the resistance of resistor R FET    222  such that sense current I SEN    208  is a relatively small fraction of the current through resistor  222 . 
     It can be shown that sense voltage V SEN    212  is given by: 
                     V   SEN     =         I   D     ⁢     R   SEN           (     1   +   K     )     +       R   SEN       R   FET                   (   1   )               
where K represents the ratio of the resistance of resistor  224  to the resistance of resistor R FET    222 . As can be seen from equation (1), sense voltage V SEN    212  (and hence, sense current I SEN    208 ) is dependent on the drain to source resistance of main transistor  202  (resistance of resistor R FET    222 ). Therefore, the ratio of the drain current of main transistor  202  to sense current I SEN    208  is also dependent on the drain to source resistance of main transistor  202 . Assuming that sense current I SEN    208  is several orders of magnitude (e.g., at least 100 times) lower than the drain current of main transistor  202  (I SEN &lt;&lt;I D ), the drain to source resistance of main transistor  202  can be approximated as:
 
                     R   FET     =       V   DS       I   D               (   2   )               
where V DS  corresponds to the voltage between the drain and the source terminals (i.e., the drain to source voltage) of main transistor  202 . Substituting this expression for resistor R FET    222  in equation (1), an alternative expression for sense voltage V SEN    212  can be obtained as follows:
 
                     V   SEN     =     1         (     1   +   K     )         I   D     ⁢     R   SEN         +     1     V   DS                   (   3   )               
This equation implies that sense current I SEN    208 , which can be obtained by dividing sense voltage V SEN    212  by the resistance of sense resistor R SEN    206 , deviates from I D /(1+K) due to the influence of the drain to source voltage of main transistor  202 . In other words, the drain to source voltage of main transistor  202  causes sense current I SEN    208  to deviate from a fixed fraction of the drain current of main transistor  202 . The amount that sense current I SEN    208  deviates from I D /(1+K) decreases with increasing drain to source voltage of main transistor  202 . To compensate for this deviation, both sense voltage V SEN    212  and the drain to source voltage of main transistor  202  may need to be measured.
 
       FIG. 2C  is a schematic of a circuit that includes an example HEMT device having a main transistor and two sense transistors. This circuit is similar to the circuit of  FIG. 2A  except that the HEMT device in  FIG. 2C  includes another HEMT as second sense transistor Q SEN2    214  for measuring the drain to source voltage of main transistor  202 . In one example, main transistor Q 1    202 , sense transistor Q SEN    204 , and second sense transistor Q SEN2    214  are Group III compound semiconductor HEMTs. Second sense transistor  214  shares drain and control terminals with those of main transistor  202 . As further shown, source terminal of second sense transistor  214  is coupled to ground reference  210  with a resistor R S    216 . If the resistance of resistor R S    216  (e.g., 10 4  ohms) is several orders of magnitude greater than the drain to source resistance of second sense transistor  214  (e.g., between 10 and 100 ohms) when second sense transistor  214  is in a saturated conductive state, then the voltage that develops across resistor R S    216  is approximately equal to the drain to source voltage of main transistor  202 . The drain to source voltage of main transistor  202  may also be referred to as a voltage V DS . Therefore, in this case, the voltage across resistor R S    216  can be used to measure the voltage V DS . 
       FIG. 3  shows example curves that represent a sense voltage representative of the drain current of the main transistor of the HEMT devices of  FIG. 2A-2C , a compensation signal, and a compensated sense voltage. Curve  312  is one possible representation of sense voltage V SEN    212  as a function of the voltage V DS . Curve  312  starts at zero when the voltage V DS  is zero volts and approaches V LIM  (where V LIM  corresponds to (I D R SEN )/(1+K)) as the voltage V DS  increases. Curve  314  is one possible representation of a compensation signal U CMP  as a voltage that is a function of the voltage V DS . Compensation signal U CMP  can be used to reduce the influence of the voltage V DS  on sense voltage V SEN    212 , and hence, reduce the influence of the drain to source resistance of main transistor  202  on sense current I SEN    208 . In one example, curve  314  is a linear ramp with a slope of −m (i.e., a linear ramp with a negative slope). Curve  316  is one possible representation of a compensated sense voltage V SENCMP  that can be obtained by adding curve  314  to curve  312 . 
     After adding the compensation signal U CMP  to sense voltage V SEN    212  given by equation (1) and manipulating the resulting expression such that the compensated sense voltage V SENCMP  has the same value for a lower limit V DSL  and a higher limit V DSH , the following expression for the compensated sense voltage V SENCMP  can be obtained: 
                     V   SENCMP     =           V   LIM     ⁢     V   NOM           V   DSL     ⁢     V   DSH         ⁢     (           (         V   DSL       V   LIM       +   1     )     ⁢     (         V   DSH       V   LIM       +   1     )           1     V   LIM       +     1     V   DS           -     V   DS       )               (   4   )               
where the lower limit V DSL  and the higher limit V DSH  represent the lower and the higher limits, respectively, of a range of values of the voltage V DS  over which the influence of the voltage V DS  on sense voltage V SEN    212  is aimed to be reduced. In equation (4), a nominal voltage V NOM  represents a value of the compensated sense voltage V SENCMP  that results in a desired ratio (e.g., 1/(1+K)) between a compensated sense current (which can be found by dividing the compensated sense voltage V SENCMP  by the resistance of sense resistor R SEN    206 ) and the drain current of main transistor  202  for the lower limit V DSL  and the higher limit V DSH . In one example, nominal voltage V NOM  is equal to V LIM  which is I D R SEN /(1+K). As further illustrated by curve  316 , the compensated voltage V SENCMP  reaches a maximum value V MAX  when the voltage V DS  equals V DSM  between the lower limit V DSL  and the higher limit V DSH . The maximum value V MAX  can be expressed as follows:
 
                     V   MAX     =           V   NOM     ⁢       V   LIM   2     ⁡     (         V   DSL       V   LIM       +   1     )       ⁢     (         V   DSH       V   LIM       +   1     )           V   DSL     ⁢     V   DSH         ⁢       (     1   -       1       (         V   DSL       V   LIM       +   1     )     ⁢     (         V   DSH       V   LIM       +   1     )             )     2               (   5   )               
In the illustrated example, the compensated sense voltage V SENCMP  may vary less with respect to the voltage V DS  when the voltage V DS  is between the lower limit V DSL  and higher limit V DSH . This means that the resulting compensated sense current may deviate less from I D /(1+K) when the drain to source resistance of main transistor  202  is between a low value of R DSL  (i.e., V DSL /I D ) and a high value of R DSH  (i.e., V DSH /I D ). In this manner, the influence of the drain to source resistance of main transistor  202  on sense current I SEN    208  can be reduced such that the ratio of the drain current of main transistor  202  to sense current I SEN    208  deviates less from the desired value of (1+K).
 
       FIG. 4A  is a circuit schematic illustrating one example implementation of a compensation circuit that outputs the compensated sense voltage. Compensation circuit  400  includes amplifying stages  410 ,  420  and a differential amplifier  430 . Amplifying stage  410  is coupled to receive the voltage across resistor R S    216  as the voltage V DS  and outputs an amplified version of the voltage V DS  to a negative input terminal of differential amplifier  430 . Amplifier  420  is coupled to receive the voltage across sense resistor R SEN    206  as sense voltage V SEN    212  and outputs an amplified version of sense voltage V SEN    212  to a positive input terminal of differential amplifier  430 . Amplifying stages  410  and  420  have respective gains of A 1  and A 2 . Differential amplifier  430  has a gain of A 3  and is coupled to output an amplified version of the difference between the signal at its positive input terminal and the signal at its negative input terminal. In other words, differential amplifier  430  outputs a signal that is equal to A 3  times (A 2 V SEN −A 1 V DS ). 
     It can be shown that if the values of A 1 , A 2 , and A 3  are chosen as follows: 
               A   1     =   1                 A   2     =       (           (     1   +   K     )     ⁢     R   DSL         R   SEN       +   1     )     ⁢     (           (     1   +   K     )     ⁢     R   DSH         R   SEN       +   1     )                       A   3     =       R   SEN   2           (     1   +   K     )     2     ⁢     R   DSL     ⁢     R   DSH           ,         
then the signal at the output of differential amplifier  430  corresponds to compensated sense voltage V SENCMP  given by equation (4). As previously explained, this signal will be equal to I D R SEN /(1+K) when the drain to source resistance of main transistor  202  is equal to the low value of R DSL  or the high value of R DSH . Accordingly, if this signal is applied to sense resistor R SEN    406  such as, for example, by coupling sense resistor R SEN    406  between the output of differential amplifier  430  and ground reference  210 , the resulting current in sense resistor R SEN    406  (which has the same value as resistor R SEN    206 ) becomes representative of the compensated sense current and equal to I D /(1+K) when the drain to source resistance of main transistor  202  is equal to the low value of R DSL  or the high value of R DSH . In addition, when the drain to source resistance of main transistor  202  varies between the low value of R DSL  and the high value of R DSH , the deviation of the compensated sense current from I D /(1+K) is less than the deviation of sense current I SEN    208  from I D /(1+K). Consequently, when the drain to source resistance of main transistor  202  varies between the low value of R DSL  and the high value of R DSH , the ratio of the drain current of main transistor  202  to the compensated sense current varies less than the ratio of the drain current of main transistor  202  to sense current I SEN    208 . In this manner, change in the ratio of the drain current of main transistor  202  to sense current I SEN    208  due to the variation in the drain to source resistance of main transistor  202  can be compensated for over a range of values of the drain to source resistance of main transistor  202 .
 
       FIG. 4B  is a circuit schematic illustrating another example implementation of the compensation circuit that outputs the compensated sense voltage. Compensation circuit  400  in  FIG. 4B  is equivalent to compensation circuit  400  in  FIG. 4A  but implemented with different gain values A 4 , A 5 , and A 6  for amplifying stages  410 ,  420  and differential amplifier  430 . With the following choices for values of A 4 , A 5  and A 6 : 
               A   4     =       R   SEN   2           (     1   +   K     )     2     ⁢     R   DSL     ⁢     R   DSH                       A   5     =         (       R   DSL     +       R   SEN       (     1   +   K     )         )     ⁢     (       R   DSH     +       R   SEN       (     1   +   K     )         )           R   DSL     ⁢     R   DSH                       A   6     =   1         
the resulting compensated sense voltage V SENCMP    416  and compensated sense current are the same as those that are described for  FIG. 4A .
 
       FIG. 4C  is a circuit schematic illustrating yet another example implementation of the compensation circuit that outputs the compensated sense voltage. Compensation circuit  400  in  FIG. 4C  includes a differential amplifier  440  having a gain of A and resistors R 1    442 , R 2    444 , R 3    446 , and R 4    448 . Differential amplifier  440  has a negative input terminal coupled to resistor R 1    442  and a positive input terminal coupled to resistor R 3    446 . Resistor R 1    442  and resistor R 3    446  are on the other end coupled to receive the voltage across resistor R S    216  and sense voltage V SEN    212 , respectively. Resistor R 2    444  is coupled between the negative input terminal and the output of differential amplifier  440  and resistor R 4    448  is coupled between the positive input terminal of differential amplifier  440  and ground reference  210 . The output of differential amplifier  440  is coupled to sense resistor  406 , which has the same value as resistor R SEN    206 . In the illustrated example, resistors R 1    442 , R 2    444 , R 3    446 , and R 4    448  and gain value A can be chosen such that the resulting compensated sense voltage V SENCMP    416  and compensated sense current are the same as those that are described for one of  FIG. 4A  and  FIG. 4B . In the example circuit of  FIG. 4C , differential amplifier  440  may be an operational amplifier with a gain value A high enough to be negligible in the computation of values for the values of resistors as is known in the art. In other words, with resistors R 1    442 , R 2    444 , R 3    446 , and R 4    448  and gain value A chosen appropriately, compensation circuit  400  in  FIG. 4C  can be made equivalent to compensation circuit  400  in one of  FIG. 4A  and  FIG. 4B . 
       FIG. 5  shows example curves that correspond to a ratio of the drain current of the main transistor of the HEMT device in  FIG. 2C  to a sense current and a ratio of the drain current of the main transistor of the HEMT device in  FIG. 2C  to a compensated sense current. The values are normalized to a desired nominal value to show the relative deviations from the desired nominal value. Curve  510  is one possible representation of the ratio of the drain current of main transistor  202  to sense current I SEN    208  as a function of the drain to source resistance of main transistor  202 . Curve  520  is one possible representation of the ratio of the drain current of main transistor  202  to the compensated sense current as a function of the drain to source resistance of main transistor  202 . The compensated sense current may be obtained by using compensation circuit  400  in one of  FIG. 4A ,  FIG. 4B , and  FIG. 4C . In the illustrated example, the low value R DSL  and the high value R DSH  of the drain to source resistance of main transistor  202  are chosen as 0.12 ohms and 0.22 ohms, respectively. In addition, the value of K, which represents the ratio of the resistance of resistor  224  to the resistance of resistor R FET    222 , is adjusted differently for curves  510  and  520  such that curve  510  and curve  520  have the same value for the high value R DSH  of the drain to source resistance of main transistor  202 . In this case, this value of curves  510  and  520  may represent the desired ratio of the drain current of main transistor  202  to sense current I SEN    208 . Also, curves  510  and  520  are normalized with respect to this value such that the numbers on the y-axis represent the corresponding ratios in terms of percentage of this value. 
     As further shown, under these conditions, curve  510  increases as the drain to source resistance of main transistor  202  decreases from the high value R DSH  of 0.22 ohms and becomes approximately equal to 110% (e.g., 111%) of the desired ratio when the drain to source resistance of main transistor  202  is equal to the low value R DSL  of 0.12 ohms. In other words, curve  510  deviates up to 11% from the desired ratio as the drain to source resistance of main transistor  202  varies between the low value R DSL  of 0.12 ohms and the high value R DSH  of 0.22 ohms. On the other hand, curve  520  has the same desired ratio when the drain to source resistance of main transistor  202  is equal to the low value R DSL  of 0.12 ohms and deviates less than 2% from the desired ratio as the drain to source resistance of main transistor  202  varies between the low value R DSL  of 0.12 ohms and the high value R DSH  of 0.22 ohms. Therefore, compensation circuit  400  in one of  FIG. 4A ,  FIG. 4B  and  FIG. 4C  can be used to generate the compensated sense current such that the variation in the ratio of the drain current of main transistor  202  to sense current I SEN    208  is reduced with respect to the variation in the drain to source resistance of main transistor  202 . 
       FIG. 6  is a schematic of another circuit that includes an example HEMT device having a main transistor and two sense transistors. The HEMT device in  FIG. 6  is similar to the HEMT device in  FIG. 2C  except that each one of main transistor  202  and sense transistors  204  and  214  are coupled to a corresponding MOSFET to form a cascode configuration. Specifically, the source terminal of main transistor  202  is coupled to the drain terminal of MOSFET Q 2    642 , the source terminal of sense transistor  204  is coupled to the drain terminal of MOSFET Q 3    644 , and the source terminal of second sense transistor  214  is coupled to the drain terminal of MOSFET Q 4    646 . In one example, main transistor  202  in  FIG. 6  may be a normally-on HEMT (e.g., a GaN based normally-on HEMT). Typically, a normally-on HEMT can be coupled to a normally-off (enhancement mode) MOSFET in a cascode configuration to ensure reliable and easy switching. In the illustrated example, normally-off MOSFETs Q 2    642 , Q 3    644 , and Q 4    646  are coupled to receive a drive signal U DR    640  at their respective control (gate) terminals. As such, drive signal U DR    640  controls the switching of MOSFETs Q 2    642 , Q 3    644 , and Q 4    646 . 
     Similar to main transistor  202  in  FIG. 2C , main transistor  202  in  FIG. 6  can use compensation circuit  400  in one of  FIG. 4A ,  FIG. 4B , and  FIG. 4C  to generate a compensated current sense signal to reduce the variation in the ratio of the drain current of main transistor  202  to sense current I SEN    208  with respect to the variation in the drain to source resistance of main transistor  202  over a range of values of the drain to source resistance of main transistor  202 . It should be noted that in the case of main transistor  202  in  FIG. 6 , the drain to source resistances of main transistor  202 , sense transistor  204 , and second sense transistor  214  also include the drain to source resistances of the corresponding MOSFETs.

Technology Classification (CPC): 6