Patent Abstract:
This invention relates to monostable and astable multivibrators in which the pulse width or frequency stability, respectively is increased by reducing the effect of the comparator input offset voltage. The reduction is accomplished by alternately reversing the input connections to the comparator.

Full Description:
CROSS-REFERENCE TO RELATED APPLICATIONS 
   The benefits of filing this invention as Provisional application for patent “MULTIVIBRATOR WITH REDUCED AVERAGE OFFSET VOLTAGE”, U.S. PTO 60/652,812 filed Feb. 15, 2005 by Fred Mirow are claimed. 

   BACKGROUND ART 
   One of the problems associated with multivibrators is that its comparator switching transition level is very sensitive to changes in ambient temperature and power supply voltage. This change causes the multivibrator to have variations in the pulse duration time or oscillation frequency. To reduce this instability some form of compensation is necessary. One of the methods used is to use a FET as a resister to control the charging time of a capacitor. The FET resistance value is controlled by a temperature dependent voltage, which varies to maintain a constant capacitor charging time. This is described in U.S. Pat. No. 4,547,749 issued to Clinton Kuo. Another method is to use a constant current source circuit, which is designed to be temperature independent, to charge and discharge a timing capacitor. This is described in U.S. Pat. No. 4,714,901 issued to Jain et al. 
   In these methods the variation in pulse width or oscillator frequency has been reduced by controlling the charging time of capacitors, but nothing has been done to correct an other large error source, the comparator input offset voltage and its sensitivity to temperature and supply voltage change. 
   SUMMARY OF THE INVENTION 
   The object of this invention are monostable and astable multivibrators in which the pulse width or frequency stability, respectively is increased by reducing the effect of the comparator input offset voltage. The reduction is accomplished by alternately reversing the input connections to the comparator. This maintains a constant average switching transition level which allows the multivibrator to maintain high stability even as power supply voltage level and operating temperature change. 
   There are many different well known multivibrator circuits, but they all use the principle of using the time period required to charge and or discharge a capacitor to one or more voltage levels to determine the output pulse width or frequency. The capacitor voltage level is sensed by one or more comparators which provide a output signal indicating if the voltage level is below or above that of a reference voltage level. In practice comparators have an internal offset voltage that changes the capacitor voltage level at which the comparators output signal changes relative to the reference voltage. This offset voltage changes the multivibrator operating frequency or pulse width since as the required capacitor voltage level changes the required charge and or discharge time changes. 
   The change in the average pulse width or oscillator frequency can be reduced by reducing the average input offset voltage of the comparators to substantially zero volts over multiple output pulses or cycles of oscillation. The difference of the individual pulse width will depend on the comparators offset voltage however the average pulse width will remain substantially constant. By applying the multivibrator output frequency signal to well known circuits such as frequency dividers a constant pulse width or duty cycle output signal can be obtained that is determined by the multivibrators average pulse width or frequency. By maintaining the comparators average input offset voltage at substantially zero volts, the pulse width or oscillator frequency stability is increased. 

   
     BRIEF DESCRIPTION OF DRAWINGS 
       FIG. 1  is a schematic representation of astable multivibrator  1  in accordance with one embodiment of the present invention. 
       FIG. 2  is a diagram illustrating various astable multivibrator  1  circuit waveforms. 
       FIG. 3  shows a simplified circuits showing the effect of offset voltage on capacitor charging time and the means to reduce this effect. 
       FIG. 4  shows the circuit of  FIG. 3  with its comparator input connections reversed. 
     Fig  5   a  and  5   b  are diagrams illustrating various circuit waveforms of Fig  3  and Fig  4 . 
       FIG. 6  is a schematic representation of monostable multivibrator  2  in accordance with one embodiment of the present invention. 
       FIG. 7  is a diagram illustrating various monostable multivibrator  2  circuit waveforms. 
   

   DETAILED DESCRIPTION 
   The present invention is directed to increasing the multivibrator average pulse width or frequency stability by reducing the average circuit value of the comparator offset voltage. As explained in detail below, the multivibrator contains at least one differential input comparator which is connected by switching means to timing and voltage reference circuits. 
     FIG. 1  shows an exemplary astable multivibrator  1  in accordance with an embodiment of the present invention. However, this invention may be applied to any multivibrator that uses one or more differential input comparators. The DC input voltage is applied to terminal  21  and powers comparators  37  and  38 , inverters  41  and  42 , R S flip flop  47 , and frequency dividers  51  and  54 . The multivibrator  1  output signal is at terminal  52 . Switching means  26 ,  32 ,  49 , and  53  may use relays or well known transistor circuits to accomplish the function. 
   Referring also to  FIG. 2 , at time A line  48  goes high (essentially equal to the DC input voltage level), timing capacitor  23  begins charging through resistor  22 . Instead of resistor  22 , it is understood that current sources could have been used. The voltage level on line  27  is connected through switch means  26  to comparator  37  non inverting input line  30  and through switch means  32  to comparator  38  inverting input line  35 . DC reference voltages are obtained from the resistor voltage divider network consisting of resistors  24 ,  25 , and  31  connected between terminal  21  and ground. The DC reference voltages on line  29  is higher than that on line  34 . Line  29  is connected through switch means  26  to comparator  37  inverting input line  28 , and line  34  through switch means  32  to comparators  38  non inverting input line  33 . 
   At time B, the voltage level of timing capacitor  23  exceeds the DC reference voltage level on line  29  plus comparator  37  offset voltage, the output of comparator  37  output on line  39  goes high. Line  39  is connected through switch means  49  to input line  45  of R S flip flop  47 , which functions as a latch, and frequency dividers  54 . R S flip flop  47  output on line  48  goes low (essentially 0 volts) and timing capacitor  23  begins being discharged through resistor  22 . Also the output of frequency dividers  54  on line  57  goes high causing switch means  32  and  53  to change connections. Comparator  38  input line  35  is now connected to line  34  and input line  33  is connected to line  27 . Line  46  is now connected to the output of inverter  42  on line  44 . The output of inverter  42  is the inverted signal level of comparator  38  output. 
   At time C, the voltage level of timing capacitor  23  is less than the DC reference voltage level on line  34  minus comparator  38  offset voltage, the output of comparator  38  output on line  40  goes low and the output of inverter  42  goes high. Line  44  is connected through switch means  53  to R S flip flop  47  and frequency dividers  51  input line  46 . R S flip flop  47  output on line  48  now goes high and timing capacitor  23  again begins being charged. Also the output of frequency dividers  51  on line  56  goes high causing switch means  26  and  49  to change connections. Comparator  37  input line  30  is now connected to line  29  and input line  28  is connected to line  27 . Line  45  is now connected to the output of inverter  41  on line  43 . The output of inverter  41  is the inverted signal level of comparator  37  output. 
   At time D, the voltage level of timing capacitor  23  exceeds the DC reference voltage level on line  29  minus comparator  37  offset voltage, the output of comparator  37  output on line  39  goes low and the output of inverter  41  goes high. Line  43  is connected through switch means  49  to line  45 . R S flip flop  47  output on line  48  goes low and timing capacitor  23  begins being discharged through resistor  22 . Also the output of frequency dividers  54  on line  57  goes low causing switch means  32  and  53  to change connections. Comparator  38  input line  35  is now connected to line  27  and input line  33  is connected to line  34 . Line  46  is now connected to the output of comparator  38  line  40 . 
   At time E, the voltage level of timing capacitor  23  is less than the DC reference voltage level on line  34  plus comparator  38  offset voltage, the output of comparator  38  output on line  40  goes high. Line  40  is connected through switch means  53  to R S flip flop  47  and frequency dividers  51  input line  46 . R S flip flop  47  output on line  48  now goes high and timing capacitor  23  again begins being charged. The output of frequency dividers  51  on line  56  goes low causing switch means  26  and  49  to change connections. Multivibrator  1  has now finished a complete cycle of operation and has returned to the same state as at time A and continues repeating the operation. 
   The invention&#39;s principle of operation is further clarified using the simplified circuits shown in  FIG. 3  and  FIG. 4  with  FIG. 5  showing various circuit waveforms. Comparator  37  in  FIG. 1  may be modeled by using comparator  69  with zero offset voltage and its actual offset voltage being represented by battery  65  in series with comparator  69  input line  66 . Comparator  69  is powered by battery  63  and battery  68  sets its threshold voltage. Current source  61  charges timing capacitor  62 . For purposes of illustration the following circuit values are used; Battery  63 =10 volts, Battery  68 =5 volts, Battery  65 =0.01 volts, current source  61 =1 ua, timing capacitor  62 =1 uf. 
   Referring now to  FIG. 3  and  FIG. 5A  at time  0  timing capacitor  62  is initially at 0 volts and begins being charged by current source  61 . The voltage level on line  66  equal the sum of the timing capacitor  62  and battery  65 . When voltage level of timing capacitor  62  exceeds 4.99 volts at time F the voltage level on line  66  exceeds the 5 volts on line  67  and the output of comparator  69  goes low. Inverter  71  is connected to comparator  69  output and the output of inverter  71  at terminal  70  goes high. The amount of time required for the timing capacitor  62  to reach 4.99 volts is 4.09×1e−6/1e−6=4.99 seconds as determined using the well know equation that the capacitor voltage equals the integral of current with time divided by capacitance. 
   Referring now to  FIG. 4  timing capacitor  62  and battery  68  are now reversed in their connection to comparator  37  and timing capacitor  62  is reset to 0 volts. At time F in  FIG. 5A  capacitor  62  begins being charged again by current source  61 . The voltage level on line  66  is 5.01 volts being equal the sum of battery  68  and battery  65 . When voltage level of timing capacitor  62  exceeds 5.01 volts at time G, the voltage level on line  64  exceeds that on line  66  and comparator  69  output at terminal  70  goes high. The amount of time required for the timing capacitor  62  to reach 5.01 volts is 5.01×1e−6/1e−6=5.01 seconds. The time interval of 0 to G is 10 seconds. The average of the two time intervals 0 to F and F to G is equal to 5 seconds. 
   Referring again to  FIG. 3  but this time comparator  37  is assumed to have zero offset voltage, and battery  65  is set to zero volts and can be ignored. Beginning at time 0 in  FIG. 5B  timing capacitor  62  is initially at 0 volts and begins being charging by current source  61 . The voltage level on line  66  equal the sum of the timing capacitor  62  and battery  65 . When voltage level of timing capacitor  62  exceeds 5.00 volts at time H, the voltage level on line  66  exceeds that on line  67  and comparator  69  output goes low. Inverter  71  is connected to comparator  69  output and the output of inverter  71  at terminal  70  goes high. The amount of time required for the timing capacitor  62  to reach 5.00 volts is 5.00×1e−6/1e−6=5.00 seconds. At time H timing capacitor  62  is again reset to 0 volts and charges to 5.00 volts at time I in another 5.00 seconds. The time interval of 0 to H is equal to that of H to I. The time interval of 0 to I is 10 seconds. The average of the two time intervals, 0 to H and H to I, is equal to 5 seconds. 
   The  FIG. 5  time interval of 0 to G obtained using a comparator  39  with non zero offset voltage is equal to the time interval of 0 to I obtained using a comparator with zero offset voltage. By reversing the connections to the input of comparator  38  the effects of offset voltage on time period and its inverse, frequency, are reduced. This circuit technique also works when current source  61  is replaced by a resistor. The reduction in timing error caused by offset voltage is less but significant because the capacitor charging time is now non linear, but becomes more linear as the peak capacitor  62  voltage level is reduced. 
     FIG. 6  shows an exemplary monostable multivibrator  2  in accordance with an embodiment of the present invention. The DC input voltage is applied to terminal  21  and powers comparators  37 , inverters  41 , R S flip flop  47 , and frequency divider  51 . The multivibrator  2  output signal is on line  48 . Switching means  26 , and  49  may use relays or well known transistor circuits to accomplish the function. 
   Referring also to  Fig.7 , at time A an initiating trigger pulse is applied to input terminal  152  which is connected to the set input of R S flip flop  47  by line  146 . This causes line  48  to go high (essentially equal to the DC input voltage level), and timing capacitor  23  begins charging through resistor  22 . Instead of resistor  22 , it is understood that current sources could have been used. The voltage level on line  27  is connected through switch means  26  to comparator  37  non inverting input line  30 . DC reference voltages are obtained from the resistor voltage divider network consisting of resistors  24 ,  25 , and  31  connected between terminal  21  and ground. The DC reference voltages on line  29  is higher than that on line  27 . Line  29  is connected through switch means  26  to comparator  37  inverting input line  28 . 
   At time B, the voltage level of timing capacitor  23  exceeds the DC reference voltage level on line  29  plus comparator  37  offset voltage, the output of comparator  37  output on line  39  goes high. Line  39  is connected through switch means  49  to input line  145  of R S flip flop  47 , which functions as a latch, and frequency divider  51 . R S flip flop  47  output on line  48  goes low (essentially 0 volts) and timing capacitor  23  begins being discharged through resistor  22 . Also the output of frequency divider  51  on line  56  goes high causing switch means  26  and  49  to change connections. Comparator  37  input line  30  is now connected to line  29  and input line  28  is connected to line  27 . Line  145  is now connected to the output of inverter  41  on line  43 . The output of inverter  41  is the inverted signal level of comparator  37  output. 
   At time C an external trigger pulse is again applied to input terminal  152 . This causes line  48  to go high (essentially equal to the DC input voltage level), timing capacitor  23  begins charging again through resistor  22  since the voltage level of timing capacitor  23  had already been discharged to essentially zero voltages between time B and C. The voltage level on line  27  is connected through switch means  26  to comparator  37  inverting input line  28 . The DC reference voltages on line  29  is higher than that on line  27 . Line  29  is connected through switch means  26  to comparator  37  non inverting input line  30 . The output of comparator  37  is connected to the input of inverter  41 . The output of inverter  41  on line  43  is now connected to line  145 . 
   At time D, the voltage level of timing capacitor  23  exceeds the DC reference voltage level on line  29  minus comparator  37  offset voltage, the output of comparator  37  output on line  39  goes low and the output of inverter  41  goes high. R S flip flop  47  output on line  48  goes low and timing capacitor  23  begins being discharged through resistor  22 . Also the output of frequency dividers  51  on line  56  goes low causing switch means  26  and  49  to change connections. Comparator  37  non inverting input line  30  is now connected to line  27  and inverting input line  28  is connected to line  29 . Line  145  is now connected to the output of comparator  37  on line  39 . Multivibrator  2  has now finished a complete cycle of operation and has returned to the same state as at time A.

Technology Classification (CPC): 7