Patent Abstract:
A gate driving circuit for driving an insulated gate switching element, including a gate charging circuit configured to charge gate capacitance of the insulated gate switching element, and a gate discharging circuit that is connected in series with the gate charging circuit and configured to discharge a charge of the gate capacitance. The gate charging circuit includes a first p-channel metal oxide semiconductor field effect transistor (MOSFET), and a first hybrid normally-on enhancement MOSFET insertion (NOEMI) circuit connected in series with a drain of the first p-channel MOSFET. The gate discharging circuit includes a first n-channel MOSFET, and a second hybrid NOEMI circuit connected in series with a drain of the first n-channel MOSFET.

Full Description:
This application is a divisional application of co-pending U.S. patent application Ser. No. 13/298,279, filed Nov. 16, 2011, which is based on and claims the benefit of priority under 35 U.S.C. §119 from Japanese Patent Application No. 2010-256757, filed on Nov. 17, 2010, the contents of which are incorporated herein by reference. 
    
    
     BACKGROUND OF THE INVENTION 
     1. Field of the Invention 
     This invention relates to a gate driving circuit for driving an insulated gate switching element. 
     2. Description of the Related Art 
     Recently, insulated gate switching elements (sometimes known as power metal oxide semiconductors, or, hereinafter, power MOSs) such as insulated gate bipolar transistors (IGBTs) and power MOS field effect transistors (power MOSFETs) have been widely used in power conversion devices, and accordingly the application of the power MOSs to hybrid vehicles, electric vehicles, and so on has recently attracted attention. 
       FIG. 8  is a circuit diagram of a gate driving circuit for driving a power MOS according to the related art. This gate driving circuit  50  includes an inverter circuit  51  having a p-channel MOSFET QP 1  and an n-channel MOSFET QN 1  connected in series (having the drains respectively connected to each other). A high potential side power supply terminal Vcc of the gate driving circuit  50  is connected to a source of a p-channel MOSFET QP 1 , and a low potential side power supply terminal GND is connected to a source of an n-channel MOSFET QN 1 . 
     An input terminal Vin of the inverter circuit  51  is connected to a gate of each of the p-channel MOSFET QP 1  and the n-channel MOSFET QN 1 . A connection point of the p-channel MOSFET QP 1  and the n-channel MOSFET QN 1  is connected to one end of a gate resistor R 1 , and the other end of the gate resistor R 1  is connected to an output terminal Vout. An anode of a diode D 1  is connected to the low potential side terminal GND, and a cathode of the diode D 1  is connected to the output terminal Vout. The diode D 1  is a protection diode for preventing an excessive voltage from being applied to the output terminal Vout. Further, a voltage Vd 1  is a voltage between the connection point of the p-channel MOSFET QP 1  and the n-channel MOSFET QN 1  and the low potential side terminal GND, and is the same as a drain-source voltage Vds 1  of the n-channel MOSFET QN 1 . 
       FIG. 9  is diagram of a main circuit using a power MOSFET as a power MOS. Here, a main circuit  60  used for an electric vehicle or the like will be described. A power supply of the main circuit  60  is different from the power supply of the gate driving circuit  50 , and a voltage of a high potential side power supply terminal Vcco of the main circuit  60  is higher than that of the high potential side power supply terminal Vcc of the gate driving circuit  50 . In the case of an electric vehicle, a load is an electric motor, and an equivalent circuit of the electric motor becomes a circuit including a resistor R 2  and an inductor L 1  connected in series. Also, the power MOSFET is an re-channel type, and herein is denoted by QN 4 . In the power MOSFET QN 4 , a gate-drain capacitance is denoted by Cgd, a gate-source capacitance is denoted by Cgs, and a drain-source capacitance is denoted by Cds. A voltage between a connection point of the inductor L 1  and the power MOSFET QN 4  and the low potential side terminal GND is denoted by Vd 3 , and is the same as a drain-source voltage Vds 4  of the power MOSFET QN 4 . 
     Next, a configuration of the main circuit  60  will be described. The high potential side power supply terminal Vcco of the main circuit  60  is connected to the resistor R 2 , a drain of the power MOSFET QN 4  is connected to the inductor L 1 , and a source of the power MOSFET QN 4  is connected to the low potential side power supply terminal GND. A gate of the power MOSFET QN 4  is connected to a gate terminal Vg. The gate-drain capacitance Cgd is provided between the gate and drain of the power MOSFET QN 4 , the gate-source capacitance Cgs is provided between the gate and source of the power MOSFET QN 4 , and the drain-source capacitance Cds is provided between the drain and source of the power MOSFET QN 4 . A gate capacitance Cg of the power MOSFET QN 4  is the same as the sum of the gate-source capacitance Cgs and the gate-drain capacitance Cgd. 
       FIG. 10  is a diagram of a circuit used for a simulation of a case where the output terminal Vout of  FIG. 8  is connected to the gate terminal Vg of the  FIG. 9 . If the n-channel MOSFET QN 1  constituting the inverter circuit  51  of the gate driving circuit  50  is turned on, and the p-channel MOSFET QP 1  is turned off, the power MOSFET QN 4  of the main circuit  60  is turned off. 
       FIG. 11  is a diagram illustrating the individual waveforms of the voltage Vd 1  which is the same as the drain-source voltage Vds 1  of the n-channel MOSFET QN 1 , a current Id 1  flowing in the n-channel MOSFET QN 1 , a voltage of the input terminal Vin, and a voltage Vd 3  which is the same as the drain-source voltage Vds 4  of the power MOSFET QN 4 , when the n-channel MOSFET QN 1  is in the ON state in  FIG. 10 . The voltage Vd 1  and the voltage Vd 3  are voltages relative to the potential of the low potential side terminal GND. 
       FIG. 12  is a diagram illustrating the waveforms of the voltage Vd 1  and a drain current Id 1  flowing in the re-channel MOSFET QN 1 , when the n-channel MOSFET QN 1  is in the ON state in  FIG. 10 . 
     If a high-potential signal is input to the input terminal Vin of  FIG. 10 , the n-channel MOSFET QN 1  constituting the gate driving circuit  50  changes to the ON state, and the potential of the output terminal Vout becomes a low level. Therefore, the power MOSFET QN 4  having the gate connected to the output terminal Vout is turned off. 
     The voltage Vd 1 , which is the same as the drain-source voltage Vds 1  of the n-channel MOSFET QN 1 , gradually decreases from the voltage of the high potential side terminal Vcc. This is because the charge accumulated in the gate capacitance Cg (=Cgs+Csd) of the power MOSFET QN 4  becomes a drain current Id 1  of the n-channel MOSFET QN 1  to be discharged to the low potential side terminal GND. As shown in a portion A, in a state in which the voltage Vd 1  (which is the same as the drain-source voltage Vds 1  of the n-channel MOSFET QN 1 ) is high, a large amount of drain current Id 1  flows. Therefore, hot-carriers are generated in the n-channel MOSFET QN 1 , which deteriorates the element characteristics of the n-channel MOSFET QN 1 . Examples of element characteristic deterioration include threshold voltage shift, a decrease in drain current, and so on. 
     As shown in  FIG. 9 , in a case where the load is a motor (shown by a reference symbol “L 1 ” in  FIG. 9 ), a surge voltage Vs is applied between the drain and source of the power MOSFET QN 4  by an induced electromotive force of the motor so that the drain-source voltage Vds 4  of the power MOSFET QN 4  increases sharply. 
     The surge voltage Vs is represented as a product of the inductance L of the inductor L 1  and a current reduction rate di/dt when the power MOSFET QN 4  is turned off. In other words, an equation of Vs=L×di/dt is established. The voltage vd 3  relative to the low potential side terminal GND (which is the same as the drain-source voltage Vds 4  of the power MOSFET QN 4 ) becomes a voltage obtained by superimposing the surge voltage Vs on the voltage of the high potential side terminal Vcco. 
     Since the gate and drain of the power MOSFET QN 4  are linked to each other through the gate-drain capacitance Cgd of the power MOSFET QN 4 , the surge voltage Vs influences the gate of the power MOSFET QN 4  so that the potential of the gate terminal Vg of the power MOSFET QN 4  increases. 
     However, at the positions where the voltage Vd 1  is increased by the influence of the drain-source voltage Vds 4  (=Vd 3 ) of the power MOSFET QN 4 , the voltage Vd 1  is decreasing as shown by a reference symbol “B” in  FIG. 12 . In simulations, the degree of the increase is small. 
     Moreover, if the inductance L of the inductor L 1  is large, the falling of the voltage Vd 1  is plateaus before it falls as shown by a dotted line C, resulting in the drain-source voltage Vds 1  (=Vd 1 ) of the n-channel MOSFET QN 1  to be maintained at a high level. Therefore, the inductance L of the inductor L 1  increases, an amount of hot-carriers generated in the n-channel MOSFET QN 1  also increases. 
     As described above, since the drain current Id 1  flows in the n-channel MOSFET QN 1  in the state in which the drain-source voltage Vds 1  (=Vd 1 ) of the n-channel MOSFET QN 1  is high, the hot-carriers are generated in the re-channel MOSFET QN 1 , and causes element characteristic deterioration. The amount of hot-carriers becomes larger as the drain-source voltage Vds 1  of the n-channel MOSFET QN 1  increases, is proportional to the drain current Id 1 , and is proportional to the sixth power of the voltage Vd 1 . 
     Therefore, when the power MOSFET QN 4  is turned off, a lot of hot-carriers are generated in the n-channel MOSFET QN 1 , so as to cause element deterioration. 
     Further, when the p-channel MOSFET QP 1  of  FIG. 8  is turned on so as to turn on the power MOSFET QN 4 , similarly, hot-carriers are generated in the p-channel MOSFET QP 1 , so as to cause element deterioration. 
     The hot-carriers are carriers (electrons and holes) that come to get energy due to a high electric field. When the hot-carriers enter a gate insulating film or the like of a MOS device, in the MOS device, the threshold voltage is shifted or the drain current decreases. That is, the hot-carriers cause element characteristic deterioration. 
     Next, a method of lowering the surge voltage Vs generated at the time of turning-off will be described. 
     For example, Japanese Patent Application Laid Open (JP-A) No. 7-99429 discloses a method of suppressing generation of a surge voltage Vs by actively increasing a gate voltage of a power MOS to allow a surge current to flow to the power MOS when the surge voltage Vs is generated. 
     Further, IEEE Journal of Solid-State Circuit, vol. SC-21, February 1986, pp. 187-192 discloses a circuit (NOEMI circuit) using a technology called normally-on enhancement MOSFET insertion (NOEMI). This circuit is a circuit including a MOSEFT, which is a normally-on enhancement MOSFET (NOEM) that is normally in an ON state, so as to suppress an amount of hot-carriers generated in a MOSFET connected in series with the NOEM. 
     The method of the JP-A No. 7-99429 is effective in protecting the power MOS. However, since the drain-source voltage Vds 1  (=Vd 1 ) of the n-channel MOSFET QN 1  constituting the gate driving circuit  50  is high, hot-carrier generation in the n-channel MOSFET QN 1  cannot be prevented by the method of JP-A No. 7-99429. 
     Also, IEEE Journal of Solid-State Circuit, vol. SC-21, February 1986, pp. 187-192 discloses that an NOEMI circuit is used in an integrated circuit such as an SRAM or a DRAM so as to suppress the generation of hot-carriers. However, it does not disclose that an NOEMI circuit is used in a gate driving circuit for driving a power MOS so as to suppress the amount of hot-carriers generated in a MOSFET constituting the gate driving circuit. 
     SUMMARY OF THE INVENTION 
     The invention was made to solve these problems, and an object of the invention is to provide a highly-reliable gate driving circuit that can be achieved by suppressing the amount of hot-carriers generated in a MOSFET. 
     In order to achieve the object, according to a first aspect of the invention, in a gate driving circuit which drives an insulated gate switching element, and includes a gate charging circuit for charging gate capacitance of the insulated gate switching element and a gate discharging circuit that is connected in series with the gate charging circuit and discharges the charge of the gate capacitance, the gate charging circuit includes a first p-channel MOSFET, and a second p-channel MOSFET having a source connected in series with a drain of the first p-channel MOSFET and constituting a first same-type NOEMI circuit, the gate discharging circuit includes a first n-channel MOSFET, and a second n-channel MOSFET having a source connected in series with a drain of the first n-channel MOSFET and constituting a second same-type NOEMI circuit, a drain of the second n-channel MOSFET is connected in series with a drain of the second p-channel MOSFET, a source of the first p-channel MOSFET is connected to a high potential side power supply terminal, a source of the first n-channel MOSFET is connected to the low potential side power supply terminal, a gate of the second p-channel MOSFET is connected to the low potential side power supply terminal, a gate of the second n-channel MOSFET is connected to the high potential side power supply terminal, the gate of the first p-channel MOSFET and a gate of the first n-channel MOSFET are connected to each other, a connection point of the gate of the first p-channel MOSFET and the gate of the first n-channel MOSFET is connected to an input terminal, and a connection point of the drain of the second p-channel MOSFET and the drain of the second n-channel MOSFET is connected to an output terminal. 
     According to a second aspect of the invention, in the first aspect, the first p-channel MOSFET, the second p-channel MOSFET, the first n-channel MOSFET, and the second n-channel MOSFET may have the same channel width. 
     According to a third aspect of the invention, in a gate driving circuit which drives an insulated gate switching element, and includes a gate charging circuit for charging gate capacitance of the insulated gate switching element and a gate discharging circuit that is connected in series with the gate charging circuit and discharges charge of the gate capacitance, the gate charging circuit includes a first p-channel MOSFET, and a first hybrid NOEMI circuit connected in series with a drain of the first p-channel MOSFET and constituting a portion of the gate charging circuit, the gate discharging circuit includes a first re-channel MOSFET, and a second hybrid NOEMI circuit connected in series with a drain of the first n-channel MOSFET and constituting a portion of the gate discharging circuit, the first hybrid NOEMI circuit includes a second p-channel MOSFET and a third n-channel MOSFET connected in parallel to each other, the second hybrid NOEMI circuit includes a second n-channel MOSFET and a third p-channel MOSFET connected in parallel to each other, each of a gate of the second p-channel MOSFET and a gate of the third p-channel MOSFET is connected to a low potential power supply side terminal, each of a gate of the second n-channel MOSFET and a gate of the third n-channel MOSFET is connected to a high potential power supply side terminal, a source of the second p-channel MOSFET is connected to the drain of the first p-channel MOSFET, a source of the third n-channel MOSFET is connected to the drain of the first n-channel MOSFET, a source of the first p-channel MOSFET is connected to the high potential power supply side terminal, a source of the first n-channel MOSFET is connected to the low potential power supply side terminal, a gate of the first p-channel MOSFET and a gate of the first n-channel MOSFET are connected to an input terminal to which an input signal is input, and a connection point of a drain of the second p-channel MOSFET and a drain of the third n-channel MOSFET is connected to an output terminal through a resistor, the output terminal being connected to a gate of the insulated gate switching element. 
     According to a fourth aspect of the invention, in the third aspect, a channel width of each of the second p-channel MOSFET and the third n-channel MOSFET constituting the first hybrid NOEMI circuit may be half the channel width of the first p-channel MOSFET, and a channel width of each of the second n-channel MOSFET and the third p-channel MOSFET constituting the second hybrid NOEMI circuit may be half the channel width of the first n-channel MOSFET. 
     According to a fifth aspect of the invention, in the first or third aspect, the gate charging circuit and the gate discharging circuit may constitute an inverter circuit. 
     According to a sixth aspect of the invention, in the first or third aspect, the insulated gate switching element may be an IGBT or a power MOSFET. 
     According to the invention, in a gate driving circuit having NOEMI circuits, same-type NOEMI circuits are connected in series with a p-channel MOSFET QP 1  constituting a gate charging circuit and an n-channel MOSFET QN 1  constituting a gate discharging circuit, respectively. Therefore, it is possible to suppress the amount of hot-carriers generated in the p-channel MOSFET QP 1 , the n-channel MOSFET QN 1 , and the NOEMI circuits. 
     Further, it is possible to further suppress the hot-carriers generated in the NOEMI circuits by replacing the same-type NOEMI circuits with the hybrid NOEMI circuits. 
     Since generation of hot-carriers is suppressed, it is possible to prevent element characteristic deterioration due to the hot-carriers and to manufacture a highly-reliable gate discharging circuit. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         FIG. 1  is a circuit diagram illustrating main portions of a gate driving circuit according to a first embodiment of the invention. 
         FIG. 2  is a diagram illustrating the waveforms of a drain voltage Vd 1  of an n-channel MOSFET QN 1 , a drain voltage Vd 2  of an n-channel MOSFET QN 2 , a drain voltage Vd 3  of a power MOSFET QN 4 , a current Id 1  of the n-channel MOSFET QN 1 , a voltage of an input terminal Vin, and a voltage of an output terminal Vout, when the n-channel MOSFET QN 1  is in an ON state. 
         FIG. 3  is a diagram illustrating the waveforms of a drain-source voltage Vds 2  (=Vd 2 −Vd 1 ) of the n-channel MOSFET QN 2 , and the current Id 1  of the n-channel MOSFET QN 1 . 
         FIG. 4  is a circuit diagram when the output terminal Vout of  FIG. 1  is connected to the gate terminal Vg of the power MOSFET QN 4  of  FIG. 9 . 
         FIG. 5  is a circuit diagram illustrating main portions of a gate driving circuit according to a second embodiment of the invention. 
         FIG. 6  is a diagram illustrating the waveforms of the voltage of the input terminal Vin, the drain voltage Vd 1  of the n-channel MOSFET QN 1 , the drain voltage Vd 2  of the re-channel MOSFET QN 2 , and the drain voltage Vd 3  of the power MOSFET QN 4 . 
         FIG. 7  is a diagram illustrating the waveforms of the drain-source voltage Vds 2  (=Vd 2 −Vd 1 ) of the n-channel MOSFET QN 2 , and the current Id 1  of the n-channel MOSFET QN 1 . 
         FIG. 8  is a circuit diagram of a gate driving circuit for driving a power MOS according to the related art. 
         FIG. 9  is a diagram of a main circuit using a power MOSFET as a power MOS. 
         FIG. 10  is a circuit diagram used in a simulation of a case where the gate terminal Vg of  FIG. 9  is connected to the output terminal Vout of  FIG. 8 . 
         FIG. 11  is a diagram illustrating the waveforms of a drain voltage Vd 1  of an n-channel MOSFET QN 1 , a current Id 1  of an n-channel MOSFET QN 1 , a voltage of an input terminal Vin, and a drain voltage Vd 3  of a power MOSFET QN 4 , when the n-channel MOSFET QN 1  is in an ON state. 
         FIG. 12  is a diagram illustrating the waveform of a drain-source voltage Vds 1  (=Vd 1 ) of the n-channel MOSFET QN 1  and the drain current Id 1  of the n-channel MOSFET QN 1 , when the n-channel MOSFET QN 1  is in an ON state. 
     
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     Modes for carrying out the invention will be described with respect to the following embodiments. Further, the identical portions to those in a configuration according to the related art are denoted by the same reference symbols. 
     [First Embodiment] 
       FIG. 1  is a circuit diagram illustrating main portions of a gate driving circuit according to a first embodiment of the invention. The gate driving circuit  10  includes an inverter circuit  11  having same-type NOEMI circuits  14  and  15 . The same-type NOEMI circuits  14  and  15  are NOEMI circuits each of which has a NOEM (a p-channel MOSFET QP 2  or an n-channel MOSFET QN 2 ) connected in series with a MOSFET (a p-channel MOSFET QP 1  or an n-channel MOSFET QN 1 ) that is a main element of the inverter circuit  11  and having the same conductivity type as the MOSFET. 
     The gate driving circuit  10  includes the inverter circuit  11 , and includes a high potential side gate charging circuit  12  (turn-on circuit) and a low potential side gate discharging circuit  13  (turn-off circuit). 
     The gate charging circuit  12  includes the p-channel MOSFETs QP 1  and QP 2 . The p-channel MOSFET QP 2  is the first same-type NOEMI circuit  14  for gate discharging which is always in an ON state. 
     The gate discharging circuit  13  includes the n-channel MOSFETs QN 1  and QN 2 . The n-channel MOSFET QN 2  is a second same-type NOEMI circuit  15  for gate charging which is always in an ON state. 
     Gates of the p-channel MOSFET QP 1  and the n-channel MOSFET QN 1  are connected to each other, and the connection point “a” is connected to an input terminal Vin. A source of the p-channel MOSFET QP 1  is connected to a high potential side terminal Vcc of a power supply, and a source of the n-channel MOSFET QN 1  is connected to a low potential side terminal GND of the power supply. Drains of the p-channel MOSFET QP 2  and the n-channel MOSFET QN 2  are connected to each other, and the connection point “b” is connected to an output terminal Vout. A gate of the p-channel MOSFET QP 2  constituting the first same-type NOEMI circuit  14  is connected to the low potential side terminal GND, and a gate of the n-channel MOSFET QN 2  constituting the second same-type NOEMI circuit  15  is connected to the high potential side terminal Vcc. 
     In  FIG. 1 , a reference symbol “Vds 1 ” represents a drain-source voltage of the n-channel MOSFET QN 1 , and a reference symbol “Vds 2 ” represents a drain-source voltage of the n-channel MOSFET QN 2 . A reference symbol “Vd 1 ” represents a voltage between a connection point of the re-channel MOSFET QN 1  and the n-channel MOSFET QN 2  and the low potential side terminal GND, and the voltage Vd 1  is equal to the drain-source voltage Vds 1 . A reference symbol “Vd 2 ” is a voltage between the connection point “b” of the p-channel MOSFET QP 2  and the n-channel MOSFET QN 2  and the low potential side terminal GND, and the voltage Vd 2  is equal to the sum of the drain-source voltage Vds 1  and the drain-source voltage Vds 2 . 
       FIG. 2  is a diagram illustrating the waveforms of the voltage Vd 1  (=Vds 1 ), the voltage Vd 2  (=Vds 1 +Vds 2 ), a voltage Vd 3  (=Vds 4 ), a current Id 1  of the n-channel MOSFET QN 1 , and a voltage of an input terminal Vin, when the n-channel MOSFET QN 1  is in an ON state. At time T 1 , an input signal to the input terminal Vin is switched from a low potential to a high potential. The voltages Vd 1 , Vd 2 , and Vd 3  are voltages relative to the potential of the low potential side terminal GND. 
       FIG. 3  is a diagram illustrating the waveforms of a voltage (=Vds 2 ) obtained by subtracting the voltage Vd 1  from the voltage Vd 2 , and the current Id 1  of the n-channel MOSFET QN 1 . Even in this case, at the time T 1 , the input signal to the input terminal Vin is switched from the low potential to the high potential. 
       FIG. 4  is a circuit diagram illustrating a state in which the output terminal Vout of  FIG. 1  is connected to the gate terminal Vg of the power MOSFET QN 4  of  FIG. 9 . This circuit was used to simulate the waveform of each portion shown in  FIGS. 2 and 3 . The size of each element used for the simulation will be described. The channel width W and channel length T of each of the n-channel MOSFET QN 1 , the n-channel MOSFET QN 2 , the p-channel MOSFET QP 1 , and the p-channel MOSFET QP 2  were set to, for example, 1000 μm and 1 μm, respectively. Further, for example, a threshold voltage Vth for the n-channel MOSFET QN 1  and the n-channel MOSFET QN 2  was set to 2 V, and a threshold voltage Vth for the p-channel MOSFET QP 1  and the p-channel MOSFET QP 2  was set to 1 V. 
     As shown in  FIG. 3 , when the n-channel MOSFET QN 1  is turned on (at time T 1 ), the drain-source voltage Vds 1  (=Vd 1 ) of the n-channel MOSFET QN 1  changes to a small value, so that the amount of hot-carriers in the n-channel MOSFET QN 1  is suppressed. Since the amount of hot-carriers decreases, the element characteristic deterioration of the n-channel MOSFET QN 1  is suppressed. 
     Further, since a gate-source voltage Vgs 2  (=Vcc−Vd 1 ) of the n-channel MOSFET QN 2  of  FIG. 4  is lower than a gate-source voltage Vgs 1  (=Vin=Vcc) of the n-channel MOSFET QN 1 , the impedance of the n-channel MOSFET QN 2  becomes larger than the impedance of the n-channel MOSFET QN 1 . Therefore, the drain-source voltage Vds 2  (=Vd 2 −Vd 1 ) of the n-channel MOSFET QN 2  is increased to be higher than the drain-source voltage Vds 1  (=Vd 1 ) of the n-channel MOSFET QN 1 . During a period in which an increase in the drain-source voltage Vds 2  is small, the generation of hot-carriers in the n-channel MOSFET QN 2  is suppressed enough, so that the element characteristic deterioration of the n-channel MOSFET QN 2  is prevented. As a result, it is possible to manufacture a highly-reliable gate driving circuit  10 . 
     However, if the drain-source voltage Vds 2  of the re-channel MOSFET QN 2  increases too much, hot-carriers are generated in the n-channel MOSFET QN 2  and thus cause element characteristic deterioration of the n-channel MOSFET QN 2 , which degrades the reliability of the gate driving circuit  10 . A measure for preventing this will be described in the next embodiment. 
     [Second Embodiment] 
       FIG. 5  is a circuit diagram illustrating the main portions of a gate driving circuit according to a second embodiment of the invention. The gate driving circuit  20  includes an inverter circuit  21  having hybrid NOEMI circuits  24  and  25 . The hybrid NOEMI circuits  24  and  25  mean NOEMI circuits each of which is obtained by connecting a NOEM (an n-channel MOSFET QN 2  or an n-channel MOSFET QN 3 ), having a conductivity type different from that of a MOSFET (a p-channel MOSFET QP 1  or an n-channel MOSFET QN 1 ) which is a main element of the inverter circuit  21 , in series with the MOSFET, and connecting the NOEM in parallel to a p-channel MOSFET (a p-channel MOSFET QP 3  or a p-channel MOSFET QP 2 ). 
     The gate driving circuit  20  includes the inverter circuit  21 , and includes a high potential side gate charging circuit  22  (turn-on circuit) and a low potential side gate discharging circuit  23  (turn-off circuit). 
     The gate charging circuit  22  includes the p-channel MOSFETs QP 1  and QP 2 , and the n-channel MOSFET QN 3 . The n-channel MOSFET QN 3  and the p-channel MOSFET QP 2  constitute the first hybrid NOEMI circuit  24  for gate charging which is always in an ON state. 
     The gate discharging circuit  23  includes the n-channel MOSFETs QN 1  and QN 2 , and the p-channel MOSFET QP 3 . The re-channel MOSFET QN 2  and the p-channel MOSFET QP 3  constitute the second hybrid NOEMI circuit  25  for gate discharging which is always in an ON state. 
     Further, a hybrid NOEMI circuit includes the first hybrid NOEMI circuit  24  and the second hybrid NOEMI circuit  25 . 
     Furthermore, the p-channel MOSFET QP 1  of the gate charging circuit  22  and the n-channel MOSFET QN 1  of the gate discharging circuit  23  are alternately turned on or off according to the potential of the input terminal Vin. 
     Moreover, the total occupied area of the n-channel MOSFET QN 3  and the p-channel MOSFET QP 2  of  FIG. 5  is equal to that of the p-channel MOSFET QP 2  of  FIG. 1 , and the occupied area of the n-channel MOSFET QN 2  and the p-channel MOSFET QP 3  of  FIG. 5  is equal to that of the n-channel MOSFET QN 2  of  FIG. 1 . 
     In other words, the areas of the first hybrid NOEMI circuit  24  or the second hybrid NOEMI circuit  25  of  FIG. 5  is the same as the area of the p-channel MOSFET QP 2  of the first same-type NOEMI circuit  14  or the area of the n-channel MOSFET QN 2  of the second same-type NOEMI circuits  15  of  FIG. 1 . 
     An operation of the gate driving circuit  20  of  FIG. 5  will be described below. 
     While a low-potential signal is input to the input terminal Vin, the p-channel MOSFET QP 1  is in an ON state, and the n-channel MOSFET QN 1  is in an OFF state. At this time, the output terminal Vout has a high potential and a charging current flows in the p-channel MOSFET QP 1 , the n-channel MOSFET QN 3 , and the p-channel MOSFET QP 2 , so as to charge the gate capacitance Cg (=Cgs+Cgd) of the power MOSFET QN 4  connected to the output terminal Vout. If doing so, the power MOSFET QN 4  changes to the ON state. 
     If the signal input to the input terminal Vin is switched from the low potential to the high potential, the p-channel MOSFET QP 1  changes to the OFF state, and the re-channel MOSFET QN 1  changes to the ON state. Then, the potential of the output terminal Vout is switched to a low potential, and a discharging current flows in the n-channel MOSFET QN 2 , the p-channel MOSFET QP 3 , and the n-channel MOSFET QN 1 , so as to discharge the charge of the gate capacitance Cg (=Cgs+Cgd) of the power MOSFET QN 4  connected to the output terminal Vout. 
     As described above, in the second same-type NOEMI circuit  15  of  FIG. 1 , when the input signal is switched from the low potential to the high potential, the gate-source voltage Vgs 2  of the n-channel MOSFET QN 2  becomes lower than the gate-source voltage Vgs 1  of the n-channel MOSFET QN 1 , and thus the drain-source voltage Vds 2  of the n-channel MOSFET QN 2 , which is an NOEM, becomes higher, so hot-carriers are easily generated. At this time, the drain-source voltage Vds 2  of the n-channel MOSFET QN 2  becomes higher than the drain-source voltage Vds 1  of the re-channel MOSFET QN 1 . 
     In contrast, in the second hybrid NOEMI circuit  25  of  FIG. 5 , when the input signal to the input terminal Vin is switched from the low potential to the high potential, a gate-source voltage Vgs 3  of the p-channel MOSFET QP 3  is the voltage of the high potential side terminal Vcc, and the gate-source voltage Vgs 1  of the n-channel MOSFET QN 1  changes to the high potential (=Vcc), so that both voltages become equal to each other. Therefore, the drain-source voltages Vds 1  and Vds 2  applied to the n-channel MOSFET QN 1  and the n-channel MOSFET QN 2  which is the NOEM are equalized. As a result, the drain-source voltage Vds 2  (which is the same as a source-drain voltage of the p-channel MOSFET QP 3 ) of the n-channel MOSFET QN 2  of  FIG. 5  becomes lower than the drain-source voltage Vds 2  (which is higher than the drain-source voltage Vds 1  of the n-channel MOSFET QN 1  of  FIG. 1 ) of the n-channel MOSFET QN 2  of  FIG. 1 . Therefore, it is possible to suppress the amount of hot-carriers generated in the n-channel MOSFET QN 2  and the p-channel MOSFET QP 3  of  FIG. 5 . As the current drive capability of the p-channel MOSFET QP 3  increases, the drain-source voltage Vds 2  decreases, so that effect becomes remarkable. 
     Further, the n-channel MOSFET QN 2  functions to compensate for the decrease in the current drive capability of the p-channel MOSFET QP 3  when the potential of the output terminal Vout decreases. In a case where the re-channel MOSFET QN 2  does not exist, the gate-source voltage Vgs 3  of the p-channel MOSFET QP 3  becomes lower, and if the gate-source voltage Vgs 3  reaches a level equal to or lower than the gate threshold voltage Vth, the potential of the output terminal Vout is lowered to the potential of the low potential side terminal GND. As the potential of the output terminal Vout decreases, the gate-source voltage Vgs 2  of the n-channel MOSFET QN 2  increases, so that the current drive capability of the n-channel MOSFET QN 2  increases to compensate for the p-channel MOSFET QP 3 . In this way, it is possible to reduce the potential of the output terminal Vout to the potential of the low potential side terminal GND. 
       FIG. 6  is a diagram illustrating the waveforms of the voltage of the input terminal Vin, the voltage Vd 1  (=Vds 1 ), the voltage Vd 2  (Vds 1 +Vds 2 ), the voltage Vd 3  (Vds 4 ), and the current Id 1  of  FIG. 5 . 
       FIG. 7  is a diagram illustrating the waveforms of the voltage Vd 1  (Vds 1 ), a voltage Vds 2  (Vd 2 −Vd 1 ), and the current Id 1  of  FIG. 5 . 
       FIGS. 6 and 7  show the simulation waveforms of the voltages and the currents when the circuit of  FIG. 9  is driven by the circuit of  FIG. 5 . 
     As for the size of each element, when a reference symbol “W” represents a channel width, and a reference symbol “T” represents a channel length, for example, the re-channel MOSFET QN 1  and the p-channel MOSFET QP 1  have the channel width W of 1000 μm and the channel length T of 1 μm, and the n-channel MOSFET QN 2 , the n-channel MOSFET QN 3 , the p-channel MOSFET QP 2 , and the p-channel MOSFET QP 3  have a channel width W of 500 μm and the channel length T of 1 μm. The total area of all the hybrid NOEMI circuits (the total area of the n-channel MOSFET QN 2 , the p-channel MOSFET QP 3 , the n-channel MOSFET QN 3 , and the p-channel MOSFET QP 2 ) was set to be equal to the total area of the same-type NOEMI circuits  14  and  15  (the total area of the n-channel MOSFET QN 2  and the p-channel MOSFET QP 2 ) of  FIG. 1 . 
     The n-channel MOSFET QN 1 , the n-channel MOSFET QN 2 , and the n-channel MOSFET QN 3  have the threshold voltage of 2 V, and the p-channel MOSFET QP 1 , the p-channel MOSFET QP 2 , and the p-channel MOSFET QP 3  have the threshold voltage of 1 V. Further, the input signal to the input terminal Vin is the same as that in the simulation of  FIG. 2 , and was set so as to have a low potential until the time T 1  and the high potential after the time T 1 . 
     In the simulation waveforms of  FIG. 6 , at the time T 1 , the n-channel MOSFET QN 1  and the n-channel MOSFET QN 2  are switched from the OFF state to the ON state, similarly to the simulation waveforms of  FIG. 2  and  FIG. 6 , the voltages Vd 1  (=Vds 1 ) and Vd 2  (Vds 1 +Vds 2 ) decrease together. 
     In  FIG. 7 , the falling edge of the voltage (Vd 2 −Vd 1 ) (which is the same as the drain-source voltage Vds 2  of the n-channel MOSFET QN 2 ) immediately after the changing to the ON state becomes gentler than the falling edge of the voltage Vd 1  (which is the same as the drain-source voltage Vds 1  of the n-channel MOSFET QN 1 ). Further, the value of the voltage (Vd 2 −Vd 1 ) of  FIG. 7  becomes smaller than that of the voltage (Vd 2 −Vd 1 ) of  FIG. 3 . Furthermore, the gate-source voltage Vgs 3  of the p-channel MOSFET QP 3  and the gate-source voltage Vgs 1  of the n-channel MOSFET QN 1  are almost the same as each other (=Vcc), and the voltage of the output terminal Vout is divided into the n-channel MOSFET QN 1  and the second hybrid NOEMI circuit  25 . Therefore, in the case of  FIG. 7 , the falling edge of the drain-source voltage Vds 1  (=Vd 1 ) of the n-channel MOSFET QN 1  becomes larger than in the case of  FIG. 3  (flat waveform) after switching. 
     As a result, as shown in  FIG. 7 , the drain-source voltage Vds 2  (=Vd 2 −Vd 1 ) becomes larger than the drain-source voltage Vds 1  (=Vd 1 ). However, the magnitude of the drain-source voltage Vds 2  is smaller than that of the drain-source voltage Vds 2  (=Vd 2 −Vd 1 ) shown in  FIG. 3 . Therefore, it is possible to make the amounts of hot-carriers generated in the n-channel MOSFET QN 2  and the p-channel MOSFET QP 3  of the second hybrid NOEMI circuit  25  of  FIG. 5  smaller than the amount of hot-carriers generated in the n-channel MOSFET QN 2  of the second same-type NOEMI circuit  15  of  FIG. 1 . As a result, it is possible to prevent element characteristic deterioration of the re-channel MOSFET QN 2  and to manufacture a highly-reliable gate driving circuit  20 . 
     Further, although the first embodiment and the second embodiment have been described focusing on the gate discharging circuits  13  and  23 , the gate charging circuits  12  and  22  also have the same effects. This will be described next briefly. 
     In the case of the gate charging circuit  22 , if the power MOSFET QN 4  is turned on, the voltage Vd 3  decreases by the inductance L of the inductor L 1 . As a result, a voltage applied between the p-channel MOSFET QP 1  and the first same-type NOEMI circuit  14  or between the p-channel MOSFET QP 1  and the first hybrid NOEMI circuit  22  becomes high. However, since the most of the voltage is applied to the first same-type NOEMI circuit  14 , it is presumed that the drain-source voltage Vdsp 1  of the p-channel MOSFET QP 1  to become small, so that the generation of hot-carriers is suppressed. If the voltage applied to the first same-type NOEMI circuit  14  increases, hot-carriers are generated in the p-channel MOSFET QP 2  of the first same-type NOEMI circuit  14 . 
     However, it is possible to decrease the applied voltage by replacing the first same-type NOEMI circuit  14  with the first hybrid NOEMI circuit  22 . Therefore, the amount of hot-carriers generated in the p-channel MOSFET QP 2  and the n-channel MOSFET QN 3  of the first hybrid NOEMI circuit  22  may be smaller than that in the p-channel MOSFET QP 2  of the first same-type NOEMI circuit  14 . 
     Although the cases of using the power MOSFET as the power MOS have been described in the first embodiment and the second embodiment, the power MOS may be an IGBT. 
     Finally, it is noted that while the present invention has been particularly shown and described with reference to preferred embodiments thereof, it will be understood by those skilled in the art that the foregoing and other changes in form and details can be made therein without departing from the spirit and scope of the present invention.

Technology Classification (CPC): 7