Patent Abstract:
A rare earth magnet is observed to function as a constant flux generator until coerced. To exploit this law, a Magnetic Power Converter is configured as a figure eight shaped balanced reluctance bridge where a rare earth magnet provides a source of constant flux employed as a working fluid. One side of the bridge drives an output coil and the other side is moderated by a toroid shaped control core acting as a variable reluctance shunt with respect to the magnet. Current in the control coil determines the rate and degree of flux variation across the bridge and therefore the resultant output voltage. Due to a mitigation of Lenz effect, full output loading is not reflected in the input; this property supports real power conversion efficiencies that may have wide applications in alternative energy and green energy generation.

Full Description:
BACKGROUND AND SUMMARY 
     The present disclosure generally pertains to power converters. Power converters, such as, for example, transformers, are typically used to convert electrical energy from one circuit into a suitable form for use in another circuit. Thus, power converters may be used to regulate voltage, current, or frequency between circuits. Typical power converters often utilize one or more input or primary coils positioned around a ferromagnetic core, and one or more output coils positioned around another portion of the core. The input coils are used to produce a magnetic flux in the core, which in turn produces an electromotive force, or voltage, in the output coil. However, due to the effect of Lenz&#39;s Law, the amount of output power produced by typical power converters does not exceed the amount of input power. Accordingly, a power converter which mitigates the effect of Lenz&#39;s Law on the input coils is desired. 
     Based on a standard demagnetization curve for permanent magnets, the flux density of the permanent magnet remains relatively constant until a magnetizing force sufficient to coerce the magnet is applied to the magnet, at which point the magnetic flux density drops quickly to zero. Thus, the permanent magnet acts as a constant magnetic flux generator until coerced. Furthermore, a variation of Kirchoff&#39;s current law states that magnetic flux in a series loop is constant. Therefore, the present disclosure sets forth an application of these principles wherein a permanent magnet is used to mitigate the effect of Lenz&#39;s Law in a power converter. 
     Embodiments of the present disclosure generally pertain to a magnetic power converter. A magnetic power converter in accordance with an exemplary embodiment of the present disclosure comprises a generally figure-8 shaped magnetic core having a plurality of legs. A toroid is positioned along at least one leg of the core and a permanent magnet is positioned along at least one leg of the core to provide a plurality of magnetic flux paths through the core, forming a balanced reluctance bridge. An output coil is positioned around one leg of the core, and at least one input coil is positioned around a portion of each toroid. When current is driven through the input coil, a control flux is induced in each toroid which remains captured in the toroid, increasing the flux density in the toroid and lowering the permeability of the core such that a virtual air gap is formed in each toroid. Such control flux in the toroid displaces the magnetic flux produced by the permanent magnet such that a portion of the magnetic flux from the permanent magnet flows through the third leg of the core. 
     The change in magnetic flux flowing through the third leg induces a current in the output coil which may be used to provide electrical power to a load. Thus, the control core acts as a variable reluctance shunt with respect to the magnet and the flow of electricity and none of the energy moderating the flux through the toroid is coupled to the output coil. Accordingly, the output coil is controlled by the input coils indirectly and the effect of Lenz&#39;s Law on the input coils is mitigated. Due to the absence of the effect of Lenz&#39;s Law on the input coils, any output loading is not reflected on the input. The output power may therefore be greater than the input power. Because of this ability to amplify input power, embodiments of the present disclosure may have wide applications in alternative energy and green energy generation. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       The present disclosure can be better understood with reference to the following drawings. The elements of the drawings are not necessarily to scale relative to each other, emphasis instead being placed upon clearly illustrating the principles of the disclosure. Furthermore, like reference numerals designate corresponding parts throughout the several views. 
         FIG. 1  is a top plan view of a magnetic power converter according to an exemplary embodiment of the present disclosure. 
         FIG. 2  depicts the magnetic power converter of  FIG. 1  illustrating input and output coils. 
         FIG. 2A  depicts the input coils of  FIG. 2  coupled in series to the power source of  FIG. 2 . 
         FIG. 3  depicts magnetic flux paths within the magnetic power converter of  FIG. 2  when no current flow through the input coils. 
         FIG. 4  depicts magnetic flux paths within the magnetic power converter of  FIG. 2  when current flows through the input coils. 
         FIG. 5  is a chart relating a B-H curve for M19 electrical steel to permeability. 
         FIG. 6  is a schematic diagram depicts the load of  FIG. 2  according to an exemplary embodiment of the present disclosure. 
         FIG. 7  depicts the input power signal and the output power signal in the test of Example I. 
         FIG. 8  depicts a magnetic power converter according to another exemplary embodiment of the present disclosure. 
         FIG. 9  depicts magnetic flux paths within the magnetic power converter of  FIG. 8  when the magnet is removed and current flows through the input coils. 
         FIG. 10  depicts magnetic flux paths within the magnetic power converter of  FIG. 8  when the magnet is present and no current flows through the input coils. 
         FIG. 11  depicts magnetic flux paths within the magnetic power converter of  FIG. 8  when the magnet is present and current flows through the input coils. 
         FIG. 12  is a top plan view of a magnetic power converter according to an exemplary embodiment of the disclosure. 
         FIG. 13  is a top plan view of the top portion of the core of the magnetic power converter of  FIG. 12 . 
         FIG. 14  is a top plan view of the magnetic power converter of  FIG. 12 , with input and output coils installed. 
         FIG. 15   a  is a top plan view of a bobbin according to an exemplary embodiment of the disclosure. 
         FIG. 15   b  is a front plan view of the bobbin of  FIG. 15   a.    
         FIG. 15   c  is a cross sectional view of the bobbin of  FIG. 15   a , taken along section lines A-A of  FIG. 15   a.    
         FIG. 15   d  is a right side plan view of the bobbin of  FIG. 15   a.    
         FIG. 16   a  is a top plan view of a clamp plate according to an exemplary embodiment of the present disclosure. 
         FIG. 16   b  is a front plan view of the clamp plate of  FIG. 16   a.    
         FIG. 16   c  is a right side plan view of the clamp plate of  FIG. 16   a.    
         FIG. 17  illustrates the installation of bobbins on the pinch points of the core. 
         FIG. 18   a  is a top plan view of a right leg bobbin according to an exemplary embodiment of the disclosure. 
         FIG. 18   b  is a front plan view of the bobbin of  FIG. 18   a.    
         FIG. 18   c  is a right side plan view of the bobbin of  FIG. 18   a.    
         FIG. 19  is a top plan view of a right leg clamp plate according to an exemplary embodiment of the disclosure. 
         FIG. 20  is a top plan view of a magnetic power converter according to another exemplary embodiment of the disclosure. 
         FIG. 21  depicts magnetic flux paths within the magnetic power converter of  FIG. 20  when the magnet is present and no current flows through the input coil. 
         FIG. 22  depicts magnetic flux paths within the magnetic power converter of  FIG. 20  when the magnet is present and current flows through the input coil. 
     
    
    
     DETAILED DESCRIPTION 
       FIG. 1  is a top plan view of a magnetic power converter  10  according to an exemplary embodiment of the present disclosure. As shown by  FIG. 1 , the magnetic power converter  10  comprises a generally figure-8 shaped magnetic core  12  having a plurality of legs and a plurality of transverse pieces. In one embodiment, the core  12  comprises one-inch thick stack of 29 gauge M19 electrical steel laminations having a C5 oxide coating. However, other isotropic steels, such as, for example, M14 electrical steel, of varying thicknesses may be utilized in the core  12  in other embodiments. 
     In one embodiment, the core  12  has a left leg  14 , a right leg  16 , a middle leg  18 , an upper transverse piece  20  and a lower transverse piece  22 . The widths (w 1 ) of the left leg  14 , the right leg  16 , the middle leg  18 , the upper transverse piece  20  and the lower transverse piece  22  are substantially equal. In one embodiment, such widths (w 1 ) are approximately one inch, although other widths are possible in other embodiments. 
     The upper transverse piece  20  is substantially parallel to the lower transverse piece  22 . The left leg  14 , right leg  16 , and middle leg  18  are substantially parallel to one another and are substantially perpendicular to the upper transverse piece  20  and the lower transverse piece  22 . Further, the upper transverse piece  20 , the lower transverse piece  22 , the left leg  14 , the right leg  16 , and the middle leg  18  are disposed in substantially the same plane. 
     The left leg  14  comprises a toroid  24  having a left portion  26  and a right portion  28 , and the right leg  16  comprises a toroid  32  having a left portion  36  and a right portion  38 . The left portion  26  and the right portion  28  lie in substantially the same plane as the left leg  14 . In the embodiment depicted by  FIG. 1 , note that the core  12  is substantially symmetrical such that the orientation and dimensions of the core  12  mirror one another with respect to the middle leg  18 . Also note that the toroid  24  is substantially the same size as the toroid  32 , and each toroid  24  and  32  is symmetrical such that the respective left and right portions  26 ,  28 ,  36 , and  38  mirror one another with respect to the corresponding leg  14  and  16 . Furthermore, the widths (w 2 ) of the left portions  26  and  36  and the right portions  28  and  38  are substantially equal. For example, in one embodiment the width (w 2 ) of each left portion  26  and  36  and each right portion  28  and  38  is one-half (0.5) inches, although other widths are possible in other embodiments. 
     The left leg  14  further comprises a permanent magnet  40  positioned within the toroid  24 , and the right leg  16  further comprises a permanent magnet  42  positioned within the toroid  32 . The permanent magnets  40  and  42  induce magnetic flux through the core  12 . The permanent magnets  40  and  42  are oriented in the same direction such that the respective north poles  44  and  46  of the magnets  40  and  42  are oriented towards the upper transverse piece  20 . In one embodiment, the magnets  40  and  42  are in line with the left leg  14  and the right leg  16 , respectively, and are the same width (w 1 ) as the legs  14  and  16 . However, the magnets  40  and  42  may have different dimensions in other embodiments. In one embodiment, the permanent magnets  40  and  42  comprise rare earth magnets, such as, for example, neodymium iron boron magnets, but other types of permanent magnets  40  and  42  may be used in other embodiments. It is well-known that the permanent magnets  40  and  42  have stored potential energy (typically referred to as the “magnetic energy product”) which is measured in megagauss-oersteds (MGOe), discussed in more detail hereafter, and represents the amount of energy the magnets  40  and  42  can supply to a magnetic circuit. One MGOe is equivalent to approximately 7957.75 Joules per cubic meter (J/m 3 ). In one embodiment, the magnetic energy product of the neodymium iron boron permanent magnets  40  and  42  is fifty-two (52) MGOe, or approximately 4.13803×10 5  J/m 3 . 
     The left portion  26  of the toroid  24  comprises a pinch point  50  wherein the left portion  26  of the toroid  24  becomes narrow, and the right portion  28  of the toroid  24  also comprises a pinch point  52 . Similarly, the left portion  36  and the right portion  38  of the toroid  32  comprise pinch points  54  and  56 , respectively. In one embodiment, a ratio of the length (L) of each pinch point  50 ,  52 ,  54 ,  56  to the corresponding depth (D) of the pinch point  50 ,  52 ,  54 ,  56  along that length is 0.8:1. For example, in one embodiment, the length (L) of the pinch point  50  is 0.2 inches and the depth (D) of the pinch point  50  is 0.25 inches. However, other ratios involving different lengths and different depths are possible in other embodiments. 
     In the embodiment depicted by  FIG. 1 , the core  12  comprises an upper section  57  and a lower section  58 . The upper section  57  comprises the upper transverse piece  20  and the upper half of the toroid  24 , the upper half of the middle leg  18 , and the upper half of the toroid  32 . Note that the pinch points  50 ,  52 ,  54 ,  56  are located in the upper section  57  in the embodiment depicted by  FIG. 1  but they may be located in the lower section  58  in other embodiments. The lower section  58  comprises the lower transverse piece  22 , the lower half of the toroid  24 , the lower half of the middle leg  18 , and the lower half of the toroid  32 . The upper section  57  abuts the lower section  58  with a plurality of precision ground butt joints (J), as shown by  FIG. 1 , which allow for easy assembly. However, other types of joints are possible in other embodiments. 
       FIG. 2  depicts the magnetic power converter  10  of  FIG. 1  having a plurality of input coils and an output coil positioned around the core  12 . As shown by  FIG. 2 , the magnetic power converter  10  further comprises an input coil  60 ,  62 ,  64 ,  66  positioned around each pinch point  50 ,  52 ,  54 ,  56 , respectively. In one embodiment, each input coil  60 ,  62 ,  64 ,  66  is wound around a bobbin (not shown) comprising insulative material, such as, for example, polyoxymethylene plastic (Delrin®). [Note, therefore, that the input coils  60 ,  62 ,  64 ,  66  as shown in  FIG. 2  are schematic representations of the coils, and do not depict the actual physical topography of the coils.] The bobbins (not shown) are positioned such that the coils  60 ,  62 ,  64 ,  66  are positioned around the corresponding pinch points  50 ,  52 ,  54 ,  56 , respectively. The input coils  60 ,  62 ,  64 ,  66  are connected in series to an AC power source  59 , as is depicted by  FIG. 2A . The power source  59  is configured to provide electrical current to the input coils  60 ,  62 ,  64 ,  66 . In one embodiment, the power source  59  provides a bipolar sine wave input signal. When the power source  59  sends an input signal to the coils  60 ,  62 ,  64 ,  66 , electrical current flows through the coils  60 ,  62 ,  64 ,  66  and induces a magnetic flux in each toroid  24  and  32 ; however, no electrical current flows through the coils  60 ,  62 ,  64 ,  66  when no input signal is sent by the power source  59 . The input coils  60 ,  62 ,  64 ,  66  are configured to generate a magnetic flux in the core  12  when an electrical current passes through the coils  60 ,  62 ,  64 ,  66  (i.e. when the power source  59  provides an input signal). In one embodiment, the input coil  60  and the input coil  64  are positioned such that the electromagnetic polarity of each coil  60  and  64  is oriented towards the lower transverse piece  22 , while the input coil  62  and the input coil  66  are positioned such that the electromagnetic polarity of each coil  62  and  66  is oriented towards the upper transverse piece  20 . Thus, the input coils  60  and  62  of the toroid  24  are oriented in opposite directions and the input coils  64  and  66  of the toroid  32  are oriented in opposite directions. Such orientations are significant for demonstrating that the placement of the permanent magnets  40  and  42  mitigate the effect of Lenz&#39;s Law on the input coils  60 ,  62 ,  64 ,  66 , discussed in more detail hereafter. However, the input coils  60 ,  62 ,  64 , and  66  may be oriented in the same direction in other embodiments. 
     In one embodiment, each input coil  60 ,  62 ,  64 ,  66  comprises insulated multifurcate wiring, such as, for example, twenty-two strands of number thirty-six (36) copper wire. Such multifurcate wiring reduces the overall resistance of the coils  60 ,  62 ,  64 ,  66  while keeping the impedance of the coils  60 ,  62 ,  64 ,  66  low, increasing the total power output of the magnetic power converter  10 . Other types of insulated multifurcate wiring are possible in other embodiments. In one embodiment, each of the coils  60 ,  62 ,  64 ,  66  has 105 turns and a resistance of 0.76 Ohms (a), although different resistances and numbers of turns may be utilized in other embodiments. 
     The magnetic power converter  10  further comprises an output coil  69  positioned around the middle leg  18  of the core  12 . When a change in magnetic flux traveling through middle leg  18  occurs, an electromotive force is induced in the output coil  69  causing the output coil  69  to generate electrical power to a load  70 , described in more detail hereafter. The output coil  69  comprises insulated multifurcate wiring. In one embodiment, the output coil  69  comprises a dual coil having sixteen strands of number thirty-two (32) copper wire. Furthermore, the coil has six hundred (600) turns and a length of 5.08 centimeters (cm) in this embodiment, but different types of coils having more or fewer turns and varying lengths are possible in other embodiments. In one embodiment, the middle leg  18  of the core  12  is one inch wide, although the middle leg  18  may be narrower in other embodiments. 
     In one exemplary embodiment, the core  12  comprises M19 electrical steel and the permanent magnets  40  and  42  comprise neodymium iron boron magnets having a magnetic energy product of 52 MGOe. The length of each pinch point  50 ,  52 ,  54 ,  56  is 0.2 inches and the depth of each pinch point  50 ,  52 ,  54 ,  56  is 0.25 inches. Also, each input coil  60 ,  62 ,  64 ,  66  comprises twenty-two (22) strands of number thirty-six (36) copper wire having one hundred five (105) turns and a resistance of 0.76Ω, and the output coil  69  comprises sixteen (16) strands of number thirty-two (32) copper wire having six hundred (600) turns. Furthermore, the coils  60  and  62  are oriented in opposite directions and the coils  64  and  66  are oriented in opposite directions. Finally, no input signal is provided by the power source  59 . 
       FIG. 3  illustrates magnetic flux produced by the permanent magnets  40  and  42  when no input power is applied to the core  12 . The magnetic flux travels through the core  12  along a plurality of magnetic flux paths  74 ,  76 , and  78 . The magnetic flux path  74  moves away from the north pole  44  of the magnet  40  and up the left leg  14  to the upper transverse piece  20 . The magnetic flux path  74  further travels along the upper transverse piece  20  and down the middle leg  18  to the lower transverse piece  22 . The magnetic flux path  74  further travels along the lower transverse piece  22  towards the left leg  14  and up the left leg  14  to the south pole  45  of the magnet  40 . Approximately half of the magnetic flux produced by the magnet  40  travels along the magnetic flux path  74  when no input signal is provided by the power source  59  ( FIG. 2 ). The magnetic flux path  76  travels in a counter-clockwise direction away from the north pole  44  of the magnet  40 , through the left portion  26  of the toroid  24 , and back to the south pole  45  of the magnet  40 . Similarly, the magnetic flux path  78  travels in a clockwise direction away from the north pole  44  of the magnet  40 , through the right portion  28  of the toroid  24 , and back to the south pole  45  of the magnet  40 . Approximately one-fourth of the magnetic flux produced by the magnet  40  flows through the magnetic flux path  76  and approximately one-fourth of the magnetic flux produced by the magnet  40  flows through the magnetic flux path  78  when no input signal is provided by the power source  59 . 
     The permanent magnet  42  produces magnetic flux which travels through the core  12  along a plurality of magnetic flux paths  84 ,  86 , and  88 . When no input signal is provided by the power source  59 , the magnetic flux path  84  moves away from the north pole  46  of the magnet  42 , up the right leg  16  to the upper transverse piece  20 , and along the upper transverse piece  20  to the middle leg  18 . The magnetic flux path  84  then travels down the middle leg  18  to the lower transverse piece  22 , along the lower transverse piece  22  to the right leg  16 , and up the right leg  16  to the south pole  47  of the magnet  42 . The magnetic flux path  86  travels away from the north pole  46  of the magnet  42  in a counter-clockwise direction through the left portion  36  of the toroid  32  and back to the south pole  47  of the magnet  42 . The magnetic flux path  88  travels in a clockwise direction from the north pole  46  of the magnet  42 , through the right portion  38  of the toroid  32 , and back to the south pole  46  of the magnet  42 . When no input signal is provided by the power source  59 , approximately half of the magnetic flux produced by the magnet  42  travels along the magnetic flux path  84 , approximately one-fourth of the magnetic flux produced by the magnet  42  travels along the magnetic flux path  86 , and approximately one-fourth of the magnetic flux produced by the magnet  42  travels along the magnetic flux path  88 . Thus, the permanent magnets  40  and  42  produce a constant magnetic flux which is distributed evenly throughout the core  12  when no input signal is provided by the power source  59 . 
     In the exemplary embodiment discussed above, the magnetic flux density (B m ) in each pinch point  50 ,  52 ,  54 ,  56  is approximately 15 kilogauss (KG) and the magnetic flux density (B m ) in the middle leg  18  is approximately 9 KG when no electrical current flows through the coils  60 ,  62 ,  64 ,  66 . 
     When the power source  59  provides an input signal to the input coils  60 ,  62 ,  64 ,  66  ( FIG. 2 ), electrical current flows through the input coils  60 ,  62 ,  64 ,  66 . It is well-known in the art that a variation of the formula for calculating electrical power is:
 
 P=I   2   R  
 
where P is power, I is current, and R is resistance. Thus, when electrical current flows through the coils  60 ,  62 ,  64 ,  66 , the total input power (P in ) is defined by the equation:
 
 P   in   =I   in   2   R   in  
 
where I in  is the input current and R in  is the total input resistance. Thus, if the input current is 980 milliamps (mA) and the total input resistance of the input coils  60 ,  62 ,  64 ,  66  is 3.04 Ohms (Ω), the input power (P in ) is set forth as
 
 P   in =(980 mA) 2 ×(3.04Ω).
 
Therefore, P in  equals approximately 2.92 Watts (W).
 
       FIG. 4  illustrates flux flowing through the core  12  when input power is applied to the core  12 . When current flows through the coil  60  ( FIG. 2 ), a control flux  90  is induced in the pinch point  50  ( FIG. 2 ) which travels in the same direction as the magnetic flux path  76 . The magnetomotive force (F c1 ) produced by the coil  60  is defined by the equation
 
 F   c1 =0.4 πN   C1   I   c1  
 
where N c1  is the number of turns of the coil  60  and I c1  is the current flowing through the coil  60 . Thus, the magnetomotive force (F c1 ) produced by the coil  60  is defined by the equation
 
 F   c1 =(0.4π)×(105)×(0.980 A)
 
which equals approximately 129.3 gilberts (Gi). The magnetizing force produced by the coil  60  is set forth by the equation
 
               H     c   ⁢           ⁢   1       =       0.4   ⁢           ⁢   π   ⁢           ⁢     N     c   ⁢           ⁢   1       ⁢     I     c   ⁢           ⁢   1           L     c   ⁢           ⁢   1               
where N c1  is the number of turns (105), I c1  is the current through the coil  60  (0.980 A), and L c1  is the length of the coil  60  (0.508 centimeters (cm)). Therefore, H c1  equals approximately 254.54 oersteds (Oe).
 
       FIG. 5  depicts a B-H curve for M19 electrical steel illustrating the relationship between permeability, magnetic flux density, and magnetizing force. The control flux  90  (Φ c1 ) induced by the coil  60  is defined by the equation
 
Φ c1   =B   c1   A  
 
where B c1  is the magnetic flux density through the pinch point  50  in KG, and A is the cross-sectional area of the core  12  through the pinch point  50  in square centimeters (1.6129 cm 2 ). In one embodiment, when 980 mA of current flows through the coil  60 , the magnetic flux density (B c1 ) through the pinch point  50  equals approximately 19.3 KG. Thus, Φ c1  is approximately equal to 31,937.4 maxwells (Mx).
 
     The strong control flux  90  and the permanent magnet (PM) magnetic flux of the magnetic flux path  76  traveling in the same direction within the pinch point  50  cause the magnetic flux density in the pinch point  50  to increase such that the left portion  26  of the toroid  24  is driven to saturation. Referring to  FIG. 5 , as the magnetizing force (H) applied to the M19 electrical steel increases, the magnetic flux density (B) increases significantly until the steel approaches saturation, at which point the permeability decreases drastically. Thus, when the magnetic flux density (B c1 ) through the pinch point  50  equals approximately 19.3 KG, the relative permeability (μ) approaches zero. 
     The relationship between reluctance (R) and permeability (μ) is defined as 
             R   =     L     μ   ⁢           ⁢   A             
where L is the length of the magnetic path in centimeters (cm) and A is the cross-sectional area of the core  12  in square centimeters (cm 2 ). Thus, as the permeability decreases the reluctance increases greatly. Furthermore, as the cross-sectional area of the core  12  decreases the reluctance increases. Therefore, the combination of the small cross-sectional area (A) of the pinch point  50  and the low permeability (μ) in the pinch point  50  causes a significant increase in reluctance (R) in the pinch point  50 . Accordingly, at saturation, the reluctance in the left portion  26  is high such that further PM magnetic flux cannot enter the left portion  26  of the toroid  24 . Such low permeability creates a virtual air gap which causes a significant amount of the magnetic flux of the PM magnetic flux path  76  to flow through the magnetic flux path  74 .
 
     Furthermore, as shown by  FIG. 4 , when current flows through the coil  62  ( FIG. 2 ), a control flux  92  is induced in the pinch point  52  ( FIG. 2 ) which opposes the magnetic flux of the magnetic flux path  78 . The control flux  92  (Φ c2 ) is generally the same magnitude as the control flux  90 , which is 31,937.4 Mx. The magnetomotive force (F c2 ), the magnetizing force (H c2 ), and the magnetic flux density (B c2 ) introduced by the coil  62  are also equal in magnitude to F c1 , H c1 , and B c1 , respectively, but in an opposite direction with respect to the permanent magnet  40 . The control flux  92  opposes the magnetic flux in the pinch point  52 , lowering the permeability in the right portion  28  of the toroid  24  such that no flux travels through the right portion  28  and the magnetic flux density through the pinch point  52  becomes zero. Such a low permeability in the right portion  38  of the toroid  24  causes a high reluctance in the right portion  38 , creating a virtual air gap which diverts a significant amount of PM magnetic flux from the magnetic flux path  78  to the magnetic flux path  74 . A combination of the left portion  26  of the toroid  24  being driven to saturation and the right portion  28  of the toroid  24  allowing no flux to flow through the magnetic flux path  78  creates a high reluctance in the toroid  24 , causing a high percentage of the PM magnetic flux from the magnet  40  traveling along the magnetic flux path  76  and the magnetic flux path  78  to be displaced such that the PM magnetic flux now travels along the magnetic flux path  74  through the middle leg  18 . Such an increase in magnetic flux traveling through the middle leg  18  induces an electromotive force in the output coil  69  ( FIG. 2 ), which may be used to power the load  70  ( FIG. 2 ). 
     Similarly, when current flows through the coil  64  ( FIG. 2 ), a control flux  94  is induced in the pinch point  54  ( FIG. 2 ) which opposes the PM magnetic flux of the magnetic flux path  86 . The magnitude of the control flux  94  is equal to approximately 31,937.4 Mx, as discussed above with respect to the control flux  90  and  92 . Furthermore, the magnetomotive force (F c3 ), the magnetizing force (H c3 ), and the magnetic flux density (B c3 ) introduced by the coil  64  are also equal in magnitude to F c1 , H c1 , and B c1 , respectively. The control flux  92  opposes the PM magnetic flux of the magnetic flux path  86 , lowering the permeability of the pinch point  54  and creating a virtual air gap such that no magnetic flux flows through the left portion  36  of the toroid  32 . Thus, the magnetic flux density in the left portion  36  becomes zero. Accordingly, the PM magnetic flux is diverted from the magnetic flux path  86  to the magnetic flux path  84 . 
     When current flows through the coil  66  ( FIG. 2 ), a control flux  96  is induced in the pinch point  56  ( FIG. 2 ) which travels in the same direction as the magnetic flux of the magnetic flux path  88 . The magnitude of the control flux  96  is also approximately 31,937.4 Mx, as discussed above with respect to the control flux  90 ,  92 , and  94 . The magnetomotive force (F c4 ), the magnetizing force (H c4 ), and the magnetic flux density (B c4 ) introduced by the coil  66  are also equal in magnitude to F c1 , H c1 , and B c1 , respectively. A combination of the control flux  96  and the magnetic flux of the magnetic flux path  88  flowing through the pinch point  56  causes the magnetic flux density in the pinch point  56  to increase until it reaches saturation. In one embodiment, the magnetic flux density in the pinch point  56  rises to 19.3 KG. Thus, the permeability of the pinch point  56  becomes low and the reluctance becomes high, creating a virtual air gap which causes the magnetic flux of the magnetic flux path  88  to flow through the magnetic flux path  84 . 
     When the magnetic flux from the magnetic flux paths  76 ,  78 ,  86 ,  88  is diverted through the magnetic flux paths  74  and  84 , the magnetic flux flowing through the middle leg  18  increases significantly. According to Faraday&#39;s Law of induction, the induced electromotive force in any closed circuit is equal to the time rate of change of the magnetic flux through the circuit. Thus, the change in the magnetic flux traveling through the middle leg  18  induces an electromotive force in the output coil  69 , thereby converting the potential magnetic energy of the magnets  40  and  42  into kinetic electrical energy which may be used to provide electrical power to a load  70 . In one embodiment, the output signal resembles a full wave rectified sine wave which is twice the frequency of the input signal. Such an output signal shows that the output signal is indirectly controlled by the input signal, i.e., the output signal is not coupled to the input. 
     According to Lenz&#39;s Law, the polarity of the electromotive force induced in the output coil  69  ( FIG. 2 ) by a magnetic flux is such that it produces a current whose magnetic field, or magnetizing force, opposes the original change in flux. Thus, the induced current in the output coil  69  has a magnetizing force which opposes the flux flowing through the middle leg  18 . 
     The total magnetizing force (H 1TOTAL ) produced by the input coils  60  and  62  and the magnet  40  is set forth in the equation
 
 H   1TOTAL   =H   m1   +H   c1   +H   c2  
 
where H m1  is the magnetizing force produced by the magnet  40 , H c1  is the magnetizing force produced by the input coil  60 , and H c2  is the magnetizing force produced by the input coil  62 . Similarly, the total magnetizing force (H 2TOTAL ) produced by the input coils  64  and  66  and the permanent magnet  42  is set forth in the equation
 
 H   2TOTAL   =H   m2   +H   c3   +H   c4  
 
where H m2  is the magnetizing force produced by the magnet  42 , H c3  is the magnetizing force produced by the input coil  64 , and H c4  is the magnetizing force produced by the input coil  66 .
 
     It is significant to note that the polarity of the input coil  60  and the polarity of the input coil  62  are in opposition to one another with respect to the output coil  69 , and the polarity of the input coil  64  and the polarity of the input coil  66  are also in opposition to one another with respect to the output coil  69 . Thus,
 
 H   1TOTAL   =H   m1   +H   c1   −H   c2  
 
and
 
 H   2TOTAL   =H   m2   +H   c3   +H   c4 .
 
Therefore, H c1  and H c2  cancel one another out and H c3  and H c4  cancel one another out with respect to the output coil  69  such that
 
 H   1TOTAL   =H   m1  
 
and
 
 H   2TOTAL   =H   m2 .
 
Accordingly, the magnetizing force produced by the current in the output coil  69  only opposes the flux from the magnets  40  and  42  and does not affect the input coils  60 ,  62 ,  64 ,  66  since polarities of the input coils  60  and  62  and the input coils  64  and  66  are in opposition to one another with respect to the output coil  69 . Such orientation demonstrates that the input coils  60 ,  62 ,  64 ,  66  indirectly control the output and are immune from the effect of Lenz&#39;s Law.
 
     Furthermore, the standard equation for the transformer is 
               E   out     =       4.44   ⁢           ⁢   f   ⁢           ⁢     N   out     ⁢     B   m     ⁢   A       10   8             
where E out  is the electromotive force in the output coil  69 , N out  is the frequency, N out  is the number of turns of the output coil  69 , B m  is the magnetic flux density, and A is the cross-sectional area in cm 2 . The standard equation for the magnetizing force of the output coil  69 
 
               H   out     =       0.4   ⁢           ⁢   π   ⁢           ⁢     N   out     ⁢     I   out         L   out             
where N out  is the number of turns of the output coil  69 , I out  is the current through the coil  69 , and L out  is the length of the coil  69 . Note that frequency is a component of the standard equation for the transformer but is not a component of the standard equation for magnetizing force. Thus, by increasing the frequency and maintaining the current flowing through the input coils  60 ,  62 ,  64 ,  66 , the electromotive force in the output coil  69  is increased, but the opposing magnetizing force produced by the output coil  69  remains the same.
 
       FIG. 6  is a schematic diagram depicting an exemplary embodiment of the load  70  of  FIG. 2 . In one embodiment, the load  70  comprises a variable resistor  98 , such as, for example, a potentiometer, connected between the output coil  69  and ground  99 . The maximum power output delivered to the load  70  is determined by adjusting the variable resistor  98  such that the voltage across the variable resistor  98  is equal to approximately half of the no load voltage. Once the voltage across the variable resistor  98  is half of the no load voltage, the load impedance matches the source impedance. According to the maximum power theorem, when the load impedance matches the source impedance, maximum power is transferred to the load  70 . 
     Accordingly, when the voltage across the variable resistor  98  is half the no load voltage, the current flowing through the resistor is measured. The total power output is determined by the formula
 
 P   out   =V   out   I   out  
 
where P out  is the power output, V out  is the voltage across the load  70 , and I out  is the current through the load  70 . Thus, when the no load voltage is 64 V, the variable resistor  98  is adjusted until the load voltage is approximately 32 V. The current is then measured and multiplied by the load voltage to determine the power output (P out ).
 
     Example I 
     Using the exemplary magnetic power converter  10  discussed above, a test was performed with the following parameters: 
                                                                           Input   Input                   Frequency   Power   Output Power   Power Boost           (Hz)   (W)   (W)   (%)                                        60   3.155   2.940   −6.8           70   3.079   3.011   −2.2           80   3.079   3.054   −0.8           90   3.082   3.130   1.5           100   3.053   3.180   4.2                        
Accordingly, as the input frequency increased, the output power (P out ) increased with no corresponding increase to the input power (P in ).  FIG. 7  depicts the input signal  188  applied in this test, a bipolar sine wave, and the output signal  189 , which resembles a full wave rectified sine wave floating about a reference. Note that the output frequency is double that of the input.
 
       FIG. 8  depicts a magnetic power converter  100  according to another exemplary embodiment of the present disclosure. The magnetic power converter  100  comprises a generally figure-8 shaped core  102  comprising a left leg  104 , a right leg  106 , a middle leg  108 , an upper transverse piece  110 , and a lower transverse piece  112 . The left leg  104 , the right leg  106 , and the middle leg  108  each extend from the upper transverse piece  110  to the lower transverse piece  112 . In one embodiment, the core  102  comprises a one-inch thick stack of 29 gauge M19 electrical steel laminations, but other isotropic materials, such as M14 electrical steel, involving varying depths may be utilized in the core  102  in other embodiments. The left leg  104  comprises a toroid  114  having a left portion  116  and a right portion  118 . The left portion  116  and the right portion  118  comprise pinch points  120  and  122 , respectively, wherein the toroid  114  becomes narrow. In one embodiment, a ratio of the length (L) of each pinch point  120  and  122  to the corresponding depth (D) of each pinch point  120  and  122  along that length is 0.8:1. For example, in one embodiment, the length (L) of the pinch point  120  is 0.2 inches and the depth (D) of the pinch point  120  is 0.25 inches. However, other pinch point  120  and  122  ratios involving other lengths and depths are possible in other embodiments. 
     The middle leg  108  comprises a permanent magnet  130  positioned within the middle leg  108  such that the north pole  134  of the magnet  130  is oriented towards the upper transverse piece  110  and the south pole  135  of the magnet is oriented towards the lower transverse piece  112 . The permanent magnet  130  provides a constant magnetic flux throughout the core  102 . In one embodiment, the permanent magnet  130  comprises a neodymium-iron-boron magnet having a magnetic energy product of fifty-two (52) MGOe, although other types of permanent magnets  130  having varying magnetic energy products are possible in other embodiments. The right leg  106  comprises a uniform width between the upper transverse piece  110  and the lower transverse piece  112 . In one embodiment, the right leg  106  is one inch wide, but other widths are possible in other embodiments. 
     The magnetic power converter  100  further comprises an input coil  140  positioned around the pinch point  120  and an input coil  142  positioned around the pinch point  122 . Each input coil  140  and  142  is wound around a bobbin (not shown) comprising insulative material, such as, for example, polyoxymethylene plastic (Delrin®). The bobbins (not shown) are positioned such that the coils  140  and  142  are positioned around the corresponding pinch points  120  and  122 , respectively. [Note, therefore, that the input coils  140  and  142  as shown in  FIG. 8  are schematic representations of the coils, and do not depict the actual physical topography of the coils.] The input coil  140  is positioned such that the electromagnetic polarity of the coil  140  is oriented towards the lower transverse piece  112 , and the input coil  142  is positioned such that the electromagnetic polarity of the coil  142  is oriented towards the upper transverse piece  110 . The input coils  140  and  142  are connected in series to a power source  149 . The power source  149  is configured to provide electrical current to the input coils  140  and  142 . No electrical current flows through the coils  140  and  142  when no input signal is provided by the power source  149 . However, electrical current flows through the coils  140  and  142  and induces a control flux, discussed in more detail hereafter, in the toroid  114  when an input signal is provided by the power source  149 . 
     Each input coil  140  and  142  comprises insulated multifurcate wiring. In one embodiment, each input coil  140  and  142  comprises twenty-two strands of number thirty-six (36) copper wire. However, other types of wiring involving different numbers of strands are possible in other embodiments. In one embodiment, each of the coils  140  and  142  has 105 turns and a resistance of 0.76 Ohms (Ω), although different resistances and numbers of turns may be utilized in other embodiments. 
     The magnetic power converter  100  further comprises an output coil  159  positioned around the right leg  106 . When a change in magnetic flux traveling through right leg  106  occurs, an electromotive force is induced in the output coil  159  causing the output coil  159  to generate electrical power to a load  70 . The output coil  159  comprises insulated multifurcate wiring. In one embodiment, the output coil  159  comprises a dual coil having sixteen strands of number thirty-two (32) copper wire and six hundred (600) turns, but different types of coils having more or fewer turns are possible in other embodiments. 
     In one exemplary embodiment, assume that the core  102  comprises M19 electrical steel and the permanent magnet  130  is removed from the core  102 . Further assume that the length of the pinch points  120  and  122  is 0.2 inches and the depth of the pinch points  120  and  122  is 0.25 inches. Also assume that each input coil  140  and  142  comprises twenty-two (22) strands of number thirty-six (36) copper wire having one hundred five (105) turns and a resistance of 0.76Ω, and that the output coil  159  comprises sixteen (16) strands of number thirty-two (32) copper wire having six hundred (600) turns. Furthermore, assume that the coils  140  and  142  are oriented in opposite directions with respect to the output coil  159 . Finally, assume that an input signal is provided by the power source  149  such that the power source  149  provides 980 mA of current through the input coils  140  and  142 . 
       FIG. 9  depicts the control flux traveling through the toroid  114  if the permanent magnet  130  were removed from the core  12  and power source  149  ( FIG. 8 ) were providing an input signal to the input coils  140  and  142 . As shown by  FIG. 9 , when power source  149  provides an input signal, the input coil  140  ( FIG. 8 ) induces a control flux  160  in the left portion  116  of the toroid  114 . Due to the orientation of the coil  140 , the control flux  160  travels down the left portion  116  in the direction indicated by directional arrow  164 . Furthermore, the input coil  142  ( FIG. 8 ) induces a control flux  162  in the right portion  118  of the toroid  114  which travels in the direction indicated by the directional arrow  165 . Accordingly, the control flux  160  induced by the input coil  140  and the control flux  162  induced by the input coil  142  are in opposition to one another with respect to the output coil  159  ( FIG. 8 ) but travel in the same circumferential direction within the toroid  114 . 
     When the power source  149  provides an input signal, the control flux  160  and  162  induced by the input coils  140  and  142 , respectively, thus travels in a counter-clockwise direction within the toroid  114 . Importantly, as shown by  FIG. 9 , none of the control flux  160  and  162  escapes the toroid  114  to the right leg  106 . Thus, the ability of the control flux  160  and  162  to remain captive within the toroid  114  demonstrates the magnetic isolation of the input coils  140  and  142  from the output coil  159 , which is significant in indirectly controlling the output coil  159  and thereby mitigating the effect of Lenz&#39;s Law on the input coils  140  and  142 . In other embodiments, the input coils  140  and  142  may be oriented in opposite directions such that they produce control flux which travels in a clockwise direction within the toroid  114 . 
       FIG. 10  illustrates magnetic flux produced by the permanent magnet  130  when no input power is applied to the core  102 . The permanent magnet  130  is positioned within the middle leg  108  of the core  102  and the magnet  130  comprises a neodymium iron boron magnet having a magnetic energy product of 52 MGOe. No input signal is provided by the power source  149 . As shown by  FIG. 10 , the permanent magnet  130  produces magnetic flux which travels through the core  102  along a plurality of magnetic flux paths  166 ,  168 , and  170 . The magnetic flux of the magnetic flux path  166  travels from the north pole  134  of the magnet  130 , up the middle leg  108 , along the upper transverse piece  110  to the left leg  104 , down the left leg  104  through the left portion  116  of the toroid  114 , along the lower transverse piece  112 , and up the middle leg  108  to the south pole  135 . The magnetic flux of the magnetic flux path  168  travels up from the north pole  134  of the magnet  130  along the middle leg  108  to the upper transverse piece  110 , across the upper transverse piece  110  to the left leg  104 , down the left leg  104  through the right portion  118  of the toroid  114  to the lower transverse piece  112 , and through the lower transverse piece  112  to the south pole  135  of the magnet  130  via the middle leg  108 . The magnetic flux of the magnetic flux path  170  travels away from the north pole  134  of the magnet  130 , up the middle leg  108  to the upper transverse piece  110 , along the upper transverse piece  110  to the right leg  106 , down the right leg  106  and along the lower transverse piece  112  and back up the middle leg  108  to the south pole  135  of the magnet  130 . Thus, when no input signal is provided by the power source  149 , the magnetic flux of the magnetic flux paths  166  and  168  travels in a counter-clockwise direction and the magnetic flux of the magnetic flux path  170  travels in a clockwise direction. 
     In the embodiment described above, the magnetic flux density (B m ) in the pinch point  120  is approximately 9.8 KG, the magnetic flux density (B m ) in the pinch point  122  is approximately 9.8 kilogauss (KG), and the magnetic flux density (B m ) in the right leg  106  is approximately 7.7 KG when no input signal is provided by the power source  149 . Referring to  FIG. 5 , when the magnetic flux density in the pinch points  120  and  122  is 9.8 KG, the respective relative permeability in each pinch point  120  and  122  is approximately 7,200, which is relatively high. Furthermore, when the magnetic flux density through the right leg  106  is 7.7 KG, the relative permeability through the right leg  106  is approximately 7,900, which is near the maximum permeability for M19 electrical steel. Accordingly, the reluctance through such magnetic flux paths  166 ,  168 , and  170  is low when no input power is applied to the core  102 . 
     Significantly, the core  102  is dimensioned such that the lengths of the magnetic flux paths  166 ,  168 , and  170  are approximately equal when no electrical current flows through the input coils  140  and  142 . Thus, magnetic flux traveling through the magnetic flux paths  166  and  168  travels generally the same distance as flux traveling through the magnetic flux path  170 . Such dimensions form a balanced reluctance bridge which allows the input coils  140  and  142  to be immune from the effect of Lenz&#39;s Law when no input signal is provided by the power source  149 . 
     Note however that the magnetic flux paths  166  and  168  are slightly longer than the magnetic flux path  170 . The effect of the shorter path  170  is offset by the larger cross-sectional area of the flux path  170 . 
       FIG. 11  illustrates flux flowing through the core  102  when input power is applied to the core  102 . The permanent magnet  130  is positioned within the middle leg  108  of the core  102  and the power source  149  ( FIG. 8 ) provides an input signal to the input coils  140  and  142  ( FIG. 8 ). As shown by  FIG. 11 , when the power source  149  provides an input signal, electrical current flows through each input coil  140  and  142  ( FIG. 8 ) and induces the control flux  160  and  162  in the toroid  114 . When the electrical current is relatively small, such as for example, 100 mA, the control flux  160  and  162  is relatively low, the magnetic flux density in the pinch points  120  and  122  is relatively low, and a small amount of PM magnetic flux is displaced from the toroid  114 . However, when the electrical current is increased, the control flux  160  and  162  becomes relatively high. When the electrical current flowing through the coils  140  and  142  is increased to 980 mA, the magnetizing force (H c1 ) and (H c2 ) produced by each coil  140  and  142  is equal to approximately 254.54 Oe. Furthermore, the magnetic flux density (B c1 ) and (B c2 ) through each respective pinch point  120  is approximately 17.5 KG, while the magnetic flux density through the output (B out ) is equal to only approximately 11.7 KG. Thus, each control flux (φ c1 )  160  and (Φ c2 )  162  is equal to approximately 28,207.5 Mx. Referring to  FIG. 5 , when the magnetic flux density is equal to approximately 17.5 KG, the relative permeability of the pinch points  120  and  122  is equal to approximately 60. Such low permeability causes the reluctance to become high, creating virtual air gaps in the pinch points  120  and  122 . When the magnetic flux density in the right leg  106  is equal to approximately 11.7 KG, however, the relative permeability in the right leg  106  is equal to approximately 4,800. Therefore, a significant amount of the magnetic flux produced by the permanent magnet flows through the magnetic flux path  170  rather than through the magnetic flux paths  166  and  168  since the permeability of the right leg  106  is significantly higher than the permeability of the pinch points  120  and  122  when current flows through the coils  140  and  142 . 
     When the magnetic flux from the magnetic flux paths  166  and  168  is diverted through the magnetic flux path  170 , the magnetic flux flowing through the right leg  106  increases significantly. According to Faraday&#39;s Law of induction, such a change in magnetic flux induces an electromotive force in the output coil  159 , thereby converting the potential magnetic energy of the magnet  130  into kinetic electrical energy which may be used to provide electrical power to a load  70 . 
     Furthermore, as set forth above, Lenz&#39;s Law states that the polarity of the electromotive force in the output coil  159  produces a current whose magnetizing force opposes the original change in flux. Thus, the magnitude of the opposing magnetizing force produced by the output coil  159  is equal to the magnitude of the total magnetizing force (H TOTAL ) produced by the input coils  140  and  142  and the magnet  130 . The total magnetizing force (H TOTAL ) is set forth in the equation
 
 H   TOTAL   =H   m   +H   c1   +H   c2  
 
where H m  is the magnetizing force produced by the magnet  130 , H c1  is the magnetizing force produced by the input coil  140 , and H c2  is the magnetizing force produced by the input coil  142 . As set forth above, the magnetizing force (H c1 ) produced by the input coil  140  and the magnetizing force (H c2 ) produced by the input coil  142  are equal in magnitude. However, it is significant to note that the input coils  140  and  142  are opposite in polarity with respect to the output coil  159 . Thus,
 
 H   TOTAL   =H   m   +H   c1   −H   c2 .
 
Since H c1  and H c2  are equal in magnitude, they cancel one another out with respect to the output coil  159  such that
 
 H   TOTAL   =H   m .
 
Accordingly, the opposing magnetizing force produced by the current in the output coil  159  only opposes the magnetizing force (H m ) of the magnet  130 , thereby effectively isolating the input coils  140  and  142  from the output coil  159  and immunizing the input coils  140  and  142  from the effect of Lenz&#39;s Law. However, due to the fact that the input coils  140  and  142  are indirectly controlling the permanent magnet  130 , the magnetizing force produced by the current in the output coil  159  only opposes the flux from the magnet  130  even if the input coils  140  and  142  are not in opposition. Thus, the opposing polarities of the input coils  140  and  142  are used to clearly demonstrate the isolation of the input coils  140  and  142  from the output coil  159 .
 
     The total input power is defined by the equation
 
 P   in   =I   in   2   R   in  
 
where I in  is the input current and R in  is the total input resistance. Thus, when the input current (I in ) is equal to 980 mA, the total input power (P in ) of the magnetic power converter  100  is set forth in the equation
 
 P   in =(0.980 A) 2 ×(1.52Ω)
 
which equals approximately 1.46 W. As set forth above, frequency is a component of the standard equation for the transformer but is not a component of the standard equation for magnetizing force. Thus, by increasing the frequency of the current flowing through the input coils  140  and  142 , the electromotive force in the output coil  159  is increased, but the magnetizing force produced by the output coil  159  remains the same.
 
       FIG. 12  is a top plan view of a magnetic power converter  200  according to another exemplary embodiment of the present disclosure. This embodiment has flux patterns substantially similar to the embodiment of  FIGS. 8-11  discussed above, and has a slightly different physical topology. The magnetic power converter  200  comprises a generally figure-8 shaped core  202  comprising a left leg  204 , a right leg  206 , a middle leg  208 , an upper transverse piece  210 , and a lower transverse piece  212 . The left leg  204 , the right leg  206 , and the middle leg  208  each extend generally perpendicularly from the upper transverse piece  210  to the lower transverse piece  212 . 
     In one embodiment, the core  202  comprises uniformly one-inch thick stack of 29 gauge M19 electrical steel laminations. Other isotropic materials, such as M14 electrical steel, with varying depths may be utilized in the core  202  in other embodiments. The M19 electrical steel comprising the core  202  is comprised of multiple layers of 29G (0.014 inch thick) steel welded together in this embodiment. 
     The left leg  204  comprises a toroid  214  having a left portion  216  and a right portion  218 . The left portion  216  and the right portion  218  comprise pinch points  220  and  222 , respectively, wherein the toroid  214  becomes narrower. In one embodiment, a ratio of the length (L) of each pinch point  220  and  222  to the corresponding depth (D) of each pinch point  220  and  222  along that length is 0.8:1. For example, in one embodiment, the length (L) of the pinch point  220  is 0.2 inches and the depth (D) of the pinch point  220  is 0.25 inches. However, other pinch point  220  and  222  ratios involving other lengths and depths are possible in other embodiments. 
     The left leg  204  comprises a neck  258  disposed above the toroid  214  between the toroid  214  and the upper transverse piece  210 . The left leg  204  further comprises a neck  265  disposed below the toroid  214  between the toroid  214  and the lower transverse piece  212 . The neck has a width of approximately 1 inch in this embodiment. 
     The toroid  214  further comprises a left upper toroid surface  266  on the left portion  216  and a right upper toroid surface  267  on the right portion  218 . The left upper toroid surface  266  and the right upper toroid surface  267  are disposed beneath the neck  258 . The toroid  214  further comprises a left lower toroid surface  266   a  on the left portion  216  and a right lower toroid surface  267   a  on the right portion  218 . The left lower toroid surface  266   a  and the right lower toroid surface  267   a  are disposed above the neck  265 . 
     The left portion  216  of the toroid  214  is bounded by a left side surface  301 , which is generally flat. The right portion  218  of the toroid  214  is bounded by a right side surface  302 , which is generally flat. 
     The toroid  214  further comprises a central opening  306 , which is generally oblong and is bounded by a curved surface  262 , a curved surface  263 , a curved surface  262   a , a curved surface  263   a , an upper flat surface  304 , a lower flat surface  305 , a right vertical surface  307 , and a left vertical surface  308 . The right and left vertical surfaces  307  and  308  define the length (L) of the pinch point  222  and  220 , respectively. 
     The middle leg  208  comprises a permanent magnet  230  positioned within the middle leg  208  such that the north pole  234  of the magnet  230  is oriented towards the upper transverse piece  210  and the south pole  235  of the magnet is oriented towards the lower transverse piece  212 . The permanent magnet  230  provides a constant magnetic flux throughout the core  202 . In one embodiment, the permanent magnet  230  comprises a one inch cube of neodymium-iron-boron magnet having a magnetic energy product of fifty-two (52) MGOe, although other types of permanent magnets  230  having varying magnetic energy products are possible in other embodiments. 
     The right leg  206  has a substantially uniform width between the upper transverse piece  210  and the lower transverse piece  212 . In one embodiment, the right leg  206  is one inch wide, but other widths are possible in other embodiments. 
     Like the embodiment shown in  FIG. 8 , the magnetic power converter  200  further comprises an input coil (not shown) positioned around the pinch point  220  and an input coil (not shown) positioned around the pinch point  222 . Each input coil is wound around a bobbin (not shown) comprising insulative material, such as, for example, polyoxymethylene plastic (Delrin®), and the input coils are in series with one another. The bobbins (not shown) are positioned such that the coils are surround the corresponding pinch points  220  and  222 . The polarity of the input coils in this embodiment is substantially similar to that of the input coils  120  and  122  of  FIG. 8 . 
     Like the embodiment shown in  FIG. 8 , the magnetic power converter  100  further comprises an output coil (not shown) positioned around the right leg  206 . When a change in magnetic flux traveling through right leg  206  occurs, an electromotive force is induced in the output coil causing the output coil to generate electrical power to a load (not shown). 
     In the illustrated embodiment, the core  202  is formed from two portions, an upper portion  203  and a lower portion  205 , which portions  203  and  205  are joined at a joint J 1  on the left portion  216  of the toroid  214 , at a joint J 2  on the right portion  218  of the toroid  214 , and at a joint J 3  on the right leg  206 . The upper portion  203  is joined to the lower portion  205  via clamps (not shown) built into the bobbins (not shown) on the left leg  204  and the right leg  206 , as further discussed herein. 
     The magnet  230  extends between a surface  275  of an extension  207  of the upper portion  203  and a surface  276  of an extension  209  on the lower portion  205 . The extension  207 , the magnet  230 , and the extension  209  form the middle leg  208 . The magnet  230  is held in place by the clamps (not shown) on the left leg  204  and the right leg  206 . 
     The upper portion  203  comprises a plurality of tooling holes  211  that extend through the core  202  and are used in assembling the upper portion  203  to the lower portion  205 . In the illustrated embodiment, the upper portion  203  comprises two (2) tooling holes  211 , though other embodiments may employ more or fewer tooling holes  211 . The tooling holes  211  in the illustrated embodiment comprise 0.255 diameter circular holes. 
     The lower portion  205  also comprises a plurality of tooling holes  213  that extend through the core  202  and are used in assembling the upper portion  203  to the lower portion  205 . In the illustrated embodiment, the lower portion  205  comprises two (2) tooling holes  213 , though other embodiments may employ more or fewer tooling holes  213 . The tooling holes  213  in the illustrated embodiment comprise 0.255 diameter circular holes. 
       FIG. 13  is a dimensioned top plan view of the top portion  203  of the core  202  ( FIG. 12 ) according to an exemplary embodiment of the disclosure. Note that the bottom portion  205  is substantially similar to and a mirror image of the top portion  203  in this embodiment. 
     The neck  258  is bounded by curved surfaces  256  and  257 . The curved surfaces  256  and  257  each comprise a 0.2 inch radius in this embodiment. The left portion  216  and the right portion  218  of the toroid  214  ( FIG. 12 ) are somewhat mirror imaged to one another. However, the left upper toroid surface  266  of the left portion  216  is slightly shorter than the right upper toroid surface  267  of the right portion  218 . In the illustrated embodiment, the upper toroid surface  266  of the left portion  216  is 0.700 wide and the upper toroid surface  267  of the right portion  218  is 0.800 wide. This difference in lengths is important because when flux (not shown) travels from the magnet  230  ( FIG. 12 ) through the left portion  216  and the right portion  218 , the flux needs to distribute equally between the left portion  216  and the right portion  218 . The flux path through the right portion  218  requires a sharper turn than the path through the left portion  216 , such that if the right portion  218  was identical to the left portion  216 , the left portion  216  would receive more flux than the right portion  218 . Shortening the upper toroid surface  266  offsets this difference and enables substantially identical flux flow through the left portion  216  and the right portion  218 . 
     The left portion  216  of the toroid  214  comprises a curved surface  262  with a 0.3 inch radius in this embodiment. The right portion  218  of the toroid  214  comprises a curved surface  263  with a 0.3 inch radius in this embodiment. 
     The extension  207  from the upper portion  203  comprises curved surfaces  259  which have a 0.4 in radius in this embodiment. Lips  260  and  261  extend from the extension  207  and bound right and left sides of the magnet  230  ( FIG. 12 ). The surface  275  bounds the north pole side of the magnet  230 . 
       FIG. 14  is a top plan view of the magnetic power converter  200  of  FIG. 12 , with a bobbin  277  installed on the left portion  216  of the toroid  214 , a bobbin  278  installed on the right portion  218  of the toroid  214 , and a right leg bobbin  279  installed on the right leg  206 . 
     The bobbins  277  and  278  each comprise a plurality of insulated multifurcate wires  280 . In one embodiment, each of the wires  280  comprises twenty-two strands of number thirty-six (36) copper wire. However, other types of wiring involving different numbers of strands are possible in other embodiments. The wires  280  on the bobbin  277  comprise a left input coil  240  on the left portion  216  ( FIG. 12 ) of the toroid  214  ( FIG. 12 ). The left input coil  240  initiates at a lead point F 1  and terminates at a lead point S 1 . The wires  280  on the bobbin  278  comprise a right input coil  242  on the right portion  218  ( FIG. 12 ) of the toroid  214  ( FIG. 12 ). The right input coil  242  initiates at a lead point F 2  and terminates at a lead point S 2 . During operation of the magnetic power converter  200 , the lead point S 1  is connected directly to the lead point S 2 , such that the input coils  240  and  242  are in series. 
     In one embodiment, each of the coils  240  and  242  has 205 turns and a resistance of 0.76 Ohms (Ω), although different resistances and numbers of turns may be utilized in other embodiments. 
     The input coils  240  and  242  are connected in series to the AC power source  259 . The power source  259  is configured to provide electrical current to the input coils  240  and  242 . In one embodiment, the power source  259  provides a bipolar sine wave input signal. 
     The right leg bobbin  279  comprises a plurality of insulated multifurcate wires  280  that make up the output coil  299 . In one embodiment, the output coil comprises insulated multifurcate wiring comprising a dual coil having sixteen strands of number thirty-two (32) copper wire and six hundred (600) turns. Different types of coils having more or fewer turns are possible in other embodiments. 
     The output coil  299  initiates at a lead point F 3  and terminates at a lead point S 3 . The output coil is connected to a load (not shown). 
       FIG. 15   a  is a top plan view of the bobbin  277  of  FIG. 15   a . Note that the bobbin  278  of  FIG. 14  is substantially similar to the bobbin  277 . An opening  805  extends through the bobbin  277  and is received by the pinch points  220  and  222  ( FIG. 12 ) when the bobbin  277  is installed on the core  202  ( FIG. 12 ). The opening  805  is centrally located in the bobbin  277  and is generally rectangular in shape. 
     The bobbin  277  further comprises a winding surface  804  that is similar in shape to the opening  805  and spaced apart from the opening  805 . The wires  280  ( FIG. 14 ) are wound around the winding surface  804 , which is generally rectangular. The dimensions of the winding surface are necessarily larger than the opening  805 . 
       FIG. 15   b  is a front plan view of the bobbin  277  of  FIG. 15   a . The bobbin  277  comprises an upper portion  806  and a lower portion  807  with an aperture  801  disposed between the upper portion  806  and the lower portion  807 . The winding surface  804  is disposed within the aperture and extends between the upper portion  806  and lower portion  807 . 
     The opening  805  extends generally vertically through the bobbin  277  and is received by the pinch points  220  and  222  ( FIG. 12 ) when the bobbin  277  is installed on the core  202  ( FIG. 12 ). In this regard, the opening  804  is generally rectangular in cross section, and is sized slightly larger than the pinch points  220  and  222 . 
     The upper portion  806  and the lower portion  807  of the bobbin  277  each comprise a plurality of openings  810  for receiving fasteners (not shown) for attaching the bobbin  277  to the core  202  ( FIG. 12 ). In this regard, the bobbin  277  acts as a clamp to join the upper portion  203  of the core  202  to the lower portion  205  of the core  202 , as further discussed herein. 
       FIG. 15   c  is a cross-sectional view of the bobbin  277  of  FIG. 15   a , taken along section lines A-A. Surface  802  defines a channel  808  ( FIG. 15   d ) that extends generally horizontally through the top portion  806  of the bobbin  277 . Surface  803  defines a channel  809  ( FIG. 15   d ) that extends generally horizontally through the bottom portion  807  of the bobbin  277 . Tapered walls  811  extend from the surfaces  802  and  803  to the opening  805  as shown. The tapered walls  811  help to guide the upper portion  203  ( FIG. 12 ) and lower portion  205  ( FIG. 12 ) of the core  202  ( FIG. 12 ) into place within the opening  805  when the bobbin  277  is being installed on the core  202 . 
       FIG. 15   d  is a side plan view of the bobbin  277  of  FIG. 15   a . The channel  808  is recessed into the top portion  806  of the bobbin  277 . Similarly, the channel  809  is recessed into the bottom portion  807  of the bobbin  277 . The width We of the channels  808  and  809  is necessarily slightly larger than the thickness of the core  202  ( FIG. 12 ), as the core  202  is disposed within the channels  808  and  809  when the bobbin  277  is installed on the core  202 . 
       FIG. 16   a  is a top plan view of a clamp plate  820  according to an embodiment of the present disclosure. Two clamp plates  820  are used to couple the bobbin  277  ( FIG. 14 ) to the core  202  ( FIG. 14 ), as further discussed herein. Similarly, two clamp plates  820  are used to couple the bobbin  278  ( FIG. 14 ) to the core  202  ( FIG. 14 ). 
     Each clamp plate  820  comprises a unitary, generally rectangular plate with a generally smooth and generally flat top surface  823  and a generally smooth and generally flat bottom surface  832  ( FIG. 16   b ). The clamp plate  820  further comprises a plurality of openings  821  extending through the plate for receiving fasteners (not shown) that couple the clamp plate  820  with the bobbin  277 . In the illustrated embodiment, the openings  821  are standard countersunk holes for receiving standard, recessed-head threaded fasteners. The openings  821  are aligned with the openings  810  ( FIG. 15   a ) in the bobbin  277  ( FIG. 15   a ). The illustrated embodiment comprises (4) openings  821  and  810 , though more or fewer openings may be employed in other embodiments. 
     The clamp plate  820  further comprises a recessed area  822  flanked by two protrusions  825  and  826  on one side of the plate  820 . The recessed area  822  receives the core  202  ( FIG. 14 ) when the clamp plate  820  is installed on the magnetic power converter  200 . The recessed area  822  has a width Wcp that is thus necessarily slightly larger than the thickness of the core  202 . An angled surface  824  extends upwardly from the bottom surface  832  ( FIG. 16   b ) of the clamp plate  820  to the top surface  823  within the recessed area  822 , as shown. A top edge and a bottom edge  829  and  827 , respectively, of the clamp plate  820  are generally straight and generally parallel to one another. A left edge  828  of the clamp plate  820  is generally straight and generally perpendicular to the top edge and bottom edge  829  and  827 . 
       FIG. 16   b  is a front side plan view of the clamp plate  820  of  FIG. 16   a . The plate  820  is generally thin and flat, as shown. 
       FIG. 16C  is a right side plan view of the clamp plate  820  of  FIG. 16   a . When the clamp  820  is installed, the bottom surface  832  contacts the top surface  830  of both the bobbin  277  and the left upper toroid surface  266  ( FIG. 12 ), as illustrated in  FIG. 17 . 
       FIG. 17  is a partial view of the magnetic power converter  200  of  FIG. 14  illustrating the installation of the clamp plates  820  and the bobbins  277  and  278  onto the core  202 . The upper portion  203  of the core  202  is joined to the lower portion  205  of the core  202  as discussed herein, and secured together by the bobbins  277 ,  278  and the clamp plates  280 . In order to assembly the magnetic power converter  200  in this fashion, the upper portion  203  and the lower portion  205  are installed into the bobbins  277  and  278  such that the pinch points  220  ( FIG. 12) and 222  ( FIG. 12 ) of the core  202  are received by the openings  805  in the bobbins  277  and  278 , respectively. The core  202  is received by the channels  808  and  809  ( FIG. 15   a ) in the bobbins  277  and  278 . 
     The clamp plates  820  are then installed by sliding the clamp plates  820  onto the left portion  216  and right portion  218  of the toroid  214  such that the bottom surfaces  832  of the clamp plates  820  rest against the toroid surfaces  266 ,  266   a ,  267 , and  267   a  of the bobbins  277  and  278 . The fasteners (not shown) are then installed through the openings  821  of the clamp plates  820  and through the openings  810  on the bobbins  277  and  278  to secure the clamp plates  820  to the bobbins  277  and  278 . When the clamp plates  820  are rigidly affixed to the bobbins  277  and  278 , the bottom surfaces  832  of the clamp plates  820  press against the toroid surfaces  266 ,  266   a ,  267 , and  267   a  of the bobbins  277  and  278  to rigidly hold the upper portion  203  and lower portion  205  of the core together. 
       FIG. 18   a  is a top plan view of the right leg bobbin  279  according to an exemplary embodiment of the present disclosure. The right leg bobbin  279  comprises a central opening  851  that extends through the bobbin  279 . The opening  851  is generally rectangular in cross section and receives the right leg  206  ( FIG. 12 ) when the upper portion  203  ( FIG. 12 ) and lower portion  205  ( FIG. 12 ) of the core  202  ( FIG. 12 ) are joined together at joint J 3  ( FIG. 12 ). The opening  851  is thus necessarily slightly larger than the right leg  206 . 
     A plurality of openings  854  receive fasteners (not shown) for coupling a right leg clamp plate  750  ( FIG. 19 ) to the right leg bobbin  850 . A channel  856  is recessed into the right leg bobbin  850  for receiving the core  202  when the right leg bobbin  840  is installed, as further discussed herein. 
       FIG. 18   b  is a front plan view of the right leg bobbin  850  of  FIG. 18   a . A winding surface  852  is disposed in the center of the bobbin  850 , and the winding surface extends between a top portion  857  and a bottom portion  858 . The winding surface  850  is generally rectangular in cross section, and the wires  280  ( FIG. 14 ) are wound against the winding surface  850 . 
       FIG. 18   c  is a right side plan view of the right leg bobbin  850  of  FIG. 18   a . The channel  856  extends across the top portion  857  and bottom portion  858  and receives the core  202  when the magnetic power converter  200  ( FIG. 14 ) is assembled. 
       FIG. 19  is a top plan view of a right leg clamp plate  750  that joins the right leg bobbin  850  to the core  202  ( FIG. 14 ). The right leg clamp plate  750  comprises a plurality of openings  855  which receive fasteners (not shown) for coupling the right leg clamp plate  750  ( FIG. 19 ) to the right leg bobbin  850 . 
     The right leg bobbin  850  and right leg clamp plates  750  are installed in a manner similar to the manner of installing the bobbins  277  and  278  to the core  202 . The right leg clamp plates  750 , when installed, apply pressure to the top portion  203  and the bottom portion  205  of the core  202  to aid in rigidly coupling the top portion  203  to the bottom portion  205 . 
       FIG. 20  is a top plan view of a magnetic power converter  900  according to another exemplary embodiment of the present disclosure. This embodiment has a similar physical structure to the embodiment depicted by  FIG. 12 . The magnetic power converter  900  comprises a generally figure-8 shaped core  902  comprising a left leg  904 , a right leg  906 , a middle leg  908 , an upper transverse piece  910 , and a lower transverse piece  912 . The left leg  904 , the right leg  906 , and the middle leg  908  each extend generally perpendicularly from the upper transverse piece  910  to the lower transverse piece  912 . 
     In one embodiment, the core  902  comprises uniformly one-inch thick stack of 29 gauge M19 electrical steel laminations. Other isotropic materials, such as M14 electrical steel, with varying depths may be utilized in the core  902  in other embodiments. The M19 electrical steel comprising the core  902  is comprised of multiple layers of 29G (0.014 inch thick) steel welded together in this embodiment. 
     The left leg  904  comprises a toroid  914  having a left portion  916  and a right portion  918 . The left portion  916  and the right portion  918  comprise pinch points  920  and  922 , respectively, wherein the toroid  214  becomes narrower. In one embodiment, a ratio of the length (L) of each pinch point  920  and  922  to the corresponding depth (D) of each pinch point  920  and  922  along that length is 0.8:1. For example, in one embodiment, the length (L) of the pinch point  920  is 0.2 inches and the depth (D) of the pinch point  920  is 0.25 inches. However, other pinch point  920  and  922  ratios involving other lengths and depths are possible in other embodiments. The other characteristics of the toroid  914  are similar to those of the toroid  214  ( FIG. 12 ) set forth above. 
     The middle leg  908  comprises a permanent magnet  930  positioned within the middle leg  908  such that the north pole  934  of the magnet  930  is oriented towards the upper transverse piece  910  and the south pole  935  of the magnet is oriented towards the lower transverse piece  912 . The permanent magnet  930  provides a constant magnetic flux throughout the core  902 . In one embodiment, the permanent magnet  930  comprises a one inch cube of neodymium-iron-boron magnet having a magnetic energy product of fifty-two (52) MGOe, although other types of permanent magnets  930  having varying magnetic energy products are possible in other embodiments. 
     The right leg  906  has a substantially uniform width between the upper transverse piece  910  and the lower transverse piece  912 . In one embodiment, the right leg  906  is one inch wide, but other widths are possible in other embodiments. Note that decreasing the cross-sectional area of the right leg  906  increases the amount of power generated by the magnetic power converter  900 . 
     The magnetic power converter  900  has a bobbin  977  installed on the left portion  916  of the toroid  914  and a right leg bobbin  979  installed on the right leg  906 . The bobbin  977  comprises a plurality of insulated multifurcate wires  980 . In one embodiment, each of the wires  980  comprises twenty-two strands of number thirty-six (36) copper wire. However, other types of wiring involving different numbers of strands are possible in other embodiments. The wires  980  on the bobbin  977  comprise an input coil  940  on the left portion  916  ( FIG. 12 ) of the toroid  914  ( FIG. 12 ). The input coil  940  initiates at a lead point F 1  and terminates at a lead point S 1 . In one embodiment, the coil  940  has 205 turns and a resistance of 0.76 Ohms (Ω), although different resistances and numbers of turns may be utilized in other embodiments. Note that the magnetic power converter  900  only comprises one input coil  940 , and the electromagnetic polarity of the coil  940  is oriented towards the upper transverse piece  910 . 
     The input coil  940  is connected to the AC power source  959  via a tank circuit (not shown). The power source  959  is configured to provide electrical current to the input coil  940 . In one embodiment, the power source  959  provides a bipolar sine wave input signal. Note that the input coil  940  should be operated at its resonance frequency. In one embodiment, the input coil  940  resonates at 500 Hz, although other frequencies are possible in other embodiments. 
     The right leg bobbin  979  comprises a plurality of insulated multifurcate wires  980  that make up the output coil  999 . In one embodiment, the output coil  999  comprises insulated multifurcate wiring comprising a dual coil having sixteen strands of number thirty-two (32) copper wire and six hundred (600) turns. Different types of coils having more or fewer turns are possible in other embodiments. 
     The output coil  999  initiates at a lead point F 2  and terminates at a lead point S 2 . The output coil  999  is connected to a load (not shown), as set forth above, via a tank circuit (not shown). The output coil  999  should also be operated at its resonance frequency. 
       FIG. 21  illustrates magnetic flux produced by the permanent magnet  930  when no input power is applied to the core  902 . The permanent magnet  930  is positioned within the middle leg  908  of the core  902  and the magnet  930  comprises a neodymium iron boron magnet having a magnetic energy product of 52 MGOe. No input signal is provided by the power source  959 . As shown by  FIG. 21 , the permanent magnet  930  produces magnetic flux which travels through the core  902  along a plurality of magnetic flux paths  966 ,  968 , and  970 . The magnetic flux of the magnetic flux path  966  travels from the north pole  934  of the magnet  930 , up the middle leg  908 , along the upper transverse piece  910  to the left leg  904 , down the left leg  904  through the left portion  916  of the toroid  914 , along the lower transverse piece  912 , and up the middle leg  908  to the south pole  935 . The magnetic flux of the magnetic flux path  968  travels up from the north pole  934  of the magnet  930  along the middle leg  908  to the upper transverse piece  910 , across the upper transverse piece  910  to the left leg  904 , down the left leg  904  through the right portion  918  of the toroid  914  to the lower transverse piece  912 , and through the lower transverse piece  912  to the south pole  935  of the magnet  930  via the middle leg  908 . The magnetic flux of the magnetic flux path  970  travels away from the north pole  934  of the magnet  930 , up the middle leg  908  to the upper transverse piece  910 , along the upper transverse piece  910  to the right leg  906 , down the right leg  906  and along the lower transverse piece  912  and back up the middle leg  908  to the south pole  935  of the magnet  930 . Thus, when no input signal is provided by the power source  959 , the magnetic flux of the magnetic flux paths  966  and  968  travels in a counter-clockwise direction and the magnetic flux of the magnetic flux path  970  travels in a clockwise direction. The reluctance through such magnetic flux paths  966 ,  968 , and  970  is low when no input power is applied to the core  902 . 
     Significantly, the core  902  is dimensioned such that the lengths of the magnetic flux paths  966 ,  968 , and  970  are approximately equal when no electrical current flows through the input coil  940 . Thus, magnetic flux traveling through the magnetic flux paths  966  and  968  travels generally the same distance as flux traveling through the magnetic flux path  970 . Such dimensions form a balanced reluctance bridge which allows the input coil  940  to be immune from the effect of Lenz&#39;s Law when an input signal is provided by the power source  949 . 
       FIG. 22  illustrates flux flowing through the core  902  of  FIG. 20  when input power is applied to the core  902 . The permanent magnet  930  is positioned within the middle leg  908  of the core  902  and the power source  959  ( FIG. 20 ) provides an input signal to the input coil  940  ( FIG. 20 ). As shown by  FIG. 22 , when the power source  959  provides an input signal, electrical current flows through the input coil  940  and induces the control flux  960  in the toroid  914 . When the electrical current is relatively small, such as for example, 100 mA, the control flux  960  is relatively low, the magnetic flux density in the pinch points  920  and  922  is relatively low, and a small amount of PM magnetic flux is displaced from the toroid  914 . However, when the electrical current is increased, the control flux  960  becomes relatively high and a majority of the control flux  960  remains captive in the toroid  914 , as shown by  FIG. 22 . The control flux  960  remains captive in the toroid  914  due to the high reluctance created by the magnet  930  along the other flux paths  970   
     When the electrical current flowing through the coil  940  is increased, the magnetic flux density increases, and the relative permeability of the pinch points  920  and  922  decreases. Such low permeability causes the reluctance to become high, creating virtual air gaps in the pinch points  920  and  922 . When the magnetic flux density in the right leg  906  is equal to approximately 11.7 KG, however, the relative permeability in the right leg  906  is relatively high, such as, for example, approximately 4,800. Therefore, a significant amount of the magnetic flux produced by the permanent magnet flows through the magnetic flux path  970  rather than through the magnetic flux paths  966  and  968  ( FIG. 21 ) since the permeability of the right leg  906  is significantly higher than the permeability of the pinch points  920  and  922  when current flows through the coil  940 . Note that the magnetic flux paths  966 ,  968  and  970  depicted by  FIGS. 21 and 22  do not represent precise physical paths through the core  902  but instead represent the general paths of the magnetic flux from the permanent magnet  930 . Thus, more magnetic flux is flowing through the right leg  906  of the core  902  when electrical current is flowing through the input coil  940  than when no electrical current is flowing through the input coil  940  because the magnetic flux that was flowing through the magnetic flux paths  966  and  968  is now flowing through the magnetic flux path  970 . 
     When the magnetic flux from the magnetic flux paths  966  and  968  is diverted through the magnetic flux path  970 , the magnetic flux flowing through the right leg  906  increases significantly. According to Faraday&#39;s Law of induction, such a change in magnetic flux induces an electromotive force in the output coil  999  ( FIG. 20 ), thereby converting the potential magnetic energy of the magnet  930  into kinetic electrical energy which may be used to provide electrical power to a load (not shown), as set forth above. 
     Furthermore, as set forth above, Lenz&#39;s Law states that the polarity of the electromotive force in the output coil  999  produces a current whose magnetizing force opposes the original change in flux. However, as shown by  FIG. 22 , the magnetic power converter  900  is a balanced reluctance bridge and the magnetic flux from the permanent magnet  930  is indirectly controlled by the input coil  940 . Therefore, the magnetizing force only opposes the magnet  930  rather than the input coil  940  since the input coil  940  is isolated from the output coil  999 . Such isolation has been demonstrated above with respect to the magnetic power converters  10 ,  100  and  200 . Furthermore, the magnetizing force required to coerce the magnet  930  is relatively high such that the output coil  999  does not produce a force sufficient to coerce the magnet  930 . 
     The total input power is defined by the equation
 
 P   in   =I   in   2   R   in  
 
where I in  is the input current and R in  is the total input resistance. Thus, when the input current (I in ) is equal to 1010 mA and the input resistance (R in ) is equal to 0.899 Ohms, the total input power (P in ) of the magnetic power converter  900  is set forth in the equation
 
 P   in =(0.1010 A) 2 ×(0.899Ω)
 
which equals approximately 0.919 W. In such embodiment, the total output power (P out ) has been measured at 10.3 W. Accordingly, by indirectly controlling the magnetic flux from the permanent magnet  930 , which is a constant magnetic flux source until coerced, power is generated in the output coil  999 .
 
     Note that the orientation of the electromagnetic polarity of the input coil  940  does not affect the performance of the magnetic power converter  900 . Thus, if the electromagnetic polarity of the input coil  940  is oriented towards the lower transverse piece  912 , the control flux  960  will complete its flux path through the permanent magnet  930 . However, none of the control flux  960  will reach the output coil  999  due to the high reluctance in the lower transverse piece  912  produced by the permanent magnet  930 , as shown by  FIG. 22 . Furthermore, as set forth above, the magnetizing force produced by the output coil  999  only opposes the magnetizing force of the permanent magnet  930  thereby mitigating the effect of Lenz&#39;s Law.

Technology Classification (CPC): 7