Patent Abstract:
A split signal pulse generator (“SSPG”) that generates a difference signal from two split signals from a splitter module, where one of the split signals may be time delayed by a delay module, where the delay module may be a transmission line having a time delay or an adjustable delay line. The SSPG may include an input amplifier configured to shape an input signal received by the splitter module. A method of generating a difference signal is also provided.

Full Description:
BACKGROUND OF THE INVENTION 
   Signal generation instruments perform many functions necessary to the testing, operation and maintenance of modern electronic applications. These signal generation instruments include pulse generators, pattern generators, data generators, pseudo-random bit sequence (“PRBS”) generators, controllable jitter injection, and timing generators. The digital waveforms and data signals generated by these instruments, such as generating digital pulses, high-speed clock signals, square waves, and flexible serial or parallel bit patterns and data streams, may be utilized in many applications requiring pulse and data generation. Applications include frequency upconversion, time-domain reflectometry, emissions testing, and phase coherency, among many other applications. 
   A typical pulse train generated by these signal generation instruments has some important features: (a) a frequency-domain spectrum with comb spacing equal to the inverse of the pulse-repetition frequency (“PRF”) rate; (b) a frequency-domain amplitude shape defined by the sinc function (with a max-to-null bandwidth equal to the inverse of the pulse width); and (c) a constant phase difference between adjacent combs. 
   However, other useful reference signals are also possible. For example, the pulse train may be modulated to spread the energy such that the peak amplitude is lower in the time domain while maintaining the same comb amplitude in the frequency domain. The pulse train may also be filtered so that only a portion of the frequency spectrum is utilized. 
     FIGS. 1A and 1B  show the time and frequency-domain descriptions  100 ,  120 , respectively, of an ideal pulse train. In  FIG. 1A , the time-domain description  100  of an ideal pulse train  102  is shown. The separation of the rising edges, Δt  104 , generally known as the pulse period, is equal to the reciprocal of the PRF, f rep    122 , where Δt=1/f rep . 
   In  FIG. 1B , the corresponding frequency-domain description  120  of the ideal pulse train is shown. That is, the periodic pulse train is Fourier-transformed. The amplitude spectrum of the pulse train consists of many equidistant spectral points  122 , which are denoted by the circles in  FIG. 1B , where the amplitude values are represented by the amplitude axis  130 . The unwrapped phase spectrum of the pulse train consists of many equidistant spectral points  123 , which are denoted by the triangles in  FIG. 1B , where the phase values are represented by the phase axis  132 . The spacing  124  of the spectral points  122  and  123  is equal to the repetition rate f rep  of the periodic pulse train. The width of the amplitude spectrum  128  until the first null, f o    126 , is determined by the pulse width, t p    106 , where f o =1/t p . The spectral width  128 , therefore, increases with decreasing pulse width. The unwrapped phase spectrum  123  is constant up to the frequency of the first null  126  in the amplitude spectrum  122 . 
   Known methods of pulse generation include the use of step-recovery diodes (“SRDs”) and non-linear transmission lines (“NLTLs”). SRDs are used for pulse generation because when switched from forward bias to reverse bias, SRDs have fast recovery time, and as a result, are capable of producing pulses with sharp and fast rise times. NLTLs are also used for pulse shaping, i.e., pulse narrowing and edge sharpening. Unfortunately, both of these methods typically have poor phase responses, have varying output level with input drive level, have high PRFs or a narrow range of PRFs, and are not easily manufactured utilizing standard surface-mount technology (which results in higher manufacturing costs). 
   Another type of pulse generator that uses logic gates and logic delay elements is disclosed in U.S. Pat. No. 4,583,008 titled “Retriggerable Edge Detector for Edge-Actuated Internally Clocked Parts” to Grugett. This type of pulse generator is typically used to create clock signals in digital circuits. Unfortunately, as pulse widths of logic circuits decrease to tens of picoseconds, digital circuit processes require reduced voltage swings. The reduced voltage swing also reduces the available signal-to-noise ratio of the ouput pulse. Another disadvantage of the logic pulse generator is that the input signal must be a square wave or pulse train. These signals, however, are difficult to generate using microwave frequency signal generators. 
   Therefore, there is a need for an improved pulse generator that has lower manufacturing costs, better phase response and output characteristics, higher signal-to-noise ratio, and that allows for PRF rates that are lower or higher than conventional pulse generators. This improved pulse generator should also be usable with input signals from conventional microwave frequency signal generators. 
   SUMMARY 
   A split signal pulse generator (“SSPG”) that includes a signal splitter, signal lines of unequal time delay, and a difference amplifier is disclosed. The SSPG may also include a DC offset in signal communication with an input of the difference amplifier that suppresses a portion of the out-going signals from the difference amplifier. The difference amplifier may be a limiting difference amplifier that limits the amplitude of the out-going signals. Additionally, the SSPG may include an input amplifier or a divider in signal communication with the SSPG. These two optional additions may improve phase noise or jitter with certain input signals and also shape certain input signals to allow a larger range of input signals to be used, such as those created by conventional microwave sources. 
   In an example of operation of the SSPG, an input signal is input to the signal splitter, which generates two output split signals. One of the split signals is time-delayed, creating an amplitude difference between the split signals at the input of the difference amplifier. The amplitude difference is amplified by the difference amplifier, which outputs one or more output signals which may be limited in amplitude. One of the outputs may be a pulse train. Additionally, the SSPG may include a DC offset that is applied between the inputs to the difference amplifier. The application of the DC offset will suppress the opposite-outgoing pulse in the output pulse train, resulting in unidirectional outgoing pulses. 
   Other systems, methods and features of the invention will be or will become apparent to one with skill in the art upon examination of the following figures and detailed description. It is intended that all such additional systems, methods, features and advantages be included within this description, be within the scope of the invention, and be protected by the accompanying claims. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
     The invention can be better understood with reference to the following figures. The components in the figures are not necessarily to scale, emphasis instead being placed upon illustrating the principles of the invention. In the figures, like reference numerals designate corresponding parts throughout the different views. 
       FIG. 1A  shows a graphical representation of an example plot of a time-domain description of an ideal pulse train. 
       FIG. 1B  shows a graphical representation of an example plot of a frequency-domain description of an ideal pulse train. 
       FIG. 2  shows a block diagram of an example of an implementation of a split signal pulse generator (“SSPG”). 
       FIG. 3  shows a schematic diagram of an example of an implementation of the SSPG shown in  FIG. 2 . 
       FIG. 4A  shows a graphical representation of an example of a plot of voltage versus time of the signals going into the difference amplifier shown in  FIG. 3 . 
       FIG. 4B  shows a graphical representation of an example of a plot of voltage versus time of the output signals from the difference amplifier shown in  FIG. 3 . 
       FIG. 5A  shows a graphical representation of an example of a plot of voltage versus time of the signals going into the difference amplifier shown in  FIG. 3  with DC offset applied. 
       FIG. 5B  shows a graphical representation of an example of a plot of voltage versus time of the output signals from the difference amplifier shown in  FIG. 3  with DC offset applied. 
       FIG. 6  shows a block diagram of an example of another implementation of the SSPG that includes an input amplifier. 
       FIG. 7  shows a block diagram of an example of yet another implementation of the SSPG shown in  FIG. 6  that includes a divider. 
       FIG. 8  shows a graphical representation of an example of a plot of a measurement of a negative pulse output of a SSPG. 
       FIG. 9  shows a graphical representation of an example of a plot of the amplitude and phase spectrum of the pulse shown in  FIG. 8 . 
       FIG. 10  shows a flow diagram of the steps performed in an example of a process of operation of the SSPG shown in  FIGS. 2 and 3 . 
   

   DETAILED DESCRIPTION 
   In the following description of the preferred embodiment, reference is made to the accompanying drawings that form a part hereof, and which show, by way of illustration, a specific embodiment in which the invention may be practiced. Other embodiments may be utilized and structural changes may be made without departing from the scope of this invention. 
   In general, the invention is a split signal pulse generator (“SSPG”) that allows pulse-repetition frequency (“PRF”) rates that are below (or above) conventional pulse generators. In an example of operation, the SSPG may operate at PRF rates that may be varied from as low as one millihertz to as high as multiple gigahertz clock rates. 
   In  FIG. 2 , a block diagram of an example of an implementation of the SSPG  200  is shown. The SSPG  200  may include a splitter module  202 , delay module  204 , and difference amplifier  206 . In this implementation example, the splitter module  202  is in signal communication with both the difference amplifier  206  and delay module  204  via signal paths  210  and  212 , respectively. The difference amplifier  206  is also in signal communication with the delay module  204  via signal path  214 . 
   In an example of operation, the SSPG  200  receives an input signal  208  at the splitter module  202  and in response, the splitter module  202  splits the input signal  208  to produce two split signals (first split signal  216  and second split signal  218 ) that are passed to difference amplifier  206  and delay module  204  via signal paths  210  and  212 , respectively. In response to receiving the second split signal  218 , the delay module  204  delays the second split signal  218  to produce a delayed split signal  220  that is passed to the difference amplifier  206  via signal path  214 . The difference amplifier  206  receives the first split signal  216  and the delayed split signal  220  and in response produces an output  222  that is a function of the voltage difference between the first split signal  216  and the delayed split signal  220 . The output  222  may be proportional to the input and may be limited in amplitude. 
   In  FIG. 3 , a schematic diagram of an example of an implementation of the SSPG  300  is shown. Similar to  FIG. 2 , the SSPG  300  may include a splitter module  302 , delay module  304 , and difference amplifier  306 . The splitter module  302  may include a splitter circuit that includes, for example, resistors  308 ,  310 , and  312 . The splitter module  302  may be in signal communication with the difference amplifier  306  via two transmission lines  314  and  316 . It is appreciated by those skilled in the art that the splitter module  302  and the delay module  304  may be passive or active and may include various types of circuitry. 
   In an example of operation, the SSPG  300  receives the input signal  318  at the splitter module  302  and in response the splitter module  302  splits the input signal  318  to produce two split signals (first split signal  320  and second split signal  322 ) that are passed to difference amplifier  306  via transmission lines  314  and  316 , respectively. It is appreciated that each transmission line  314  and  316  introduces a time delay in each split signal that is proportional to the length of the respective transmission line. As an example, the first transmission line  314  produces a first time delay on first split signal  320  to produce a first delayed split signal  324  and the second transmission line  316  produces a second time delay on the second split signal  322 , to produce a second delayed split signal  326  (i.e., such as the delayed split signal  220  in  FIG. 2 ). The first time delay is proportional to the length of the first transmission line  314  and the second time delay is proportional to the length of the second transmission line  316 . 
   If the first transmission line  314  and the second transmission line  316  are of different lengths, the length difference creates a time delay between the first delayed split signal  324  and second delayed split signal  326  that is proportional to the difference in length between the first transmission line  314  and second transmission line  316 . It is appreciated by those skilled in the art that the difference in length may be mechanically or electrically tuned by physically stretching a transmission line or by modifying the effective capacitance and inductance of a transmission line. Examples of other means of adjusting lengths of transmission lines include variable or switched delay lines, variable capacitors, and tuning stubs. 
   The difference amplifier  306  receives the resulting first delayed signal  324  and second delayed signal  326  and in response, produces two differential outputs  328  and  330  that are proportional to the voltage difference between the first delayed split signal  324  and second delayed split signal  326  and that may also be limited in amplitude. The first difference output  328  may be a positive difference output and the second difference output  330  may be a negative difference output. It is appreciated, in this example, that the second difference output  330  is optional and may be utilized as an opposite-going pulse train. 
   As an example, when input signal  318  is a square wave signal, the difference amplifier  306  produces a positive pulsed output signal at the first difference output  328  and may produce a negative pulsed output signal at the second difference output  330  upon receiving the split signals  324  and  326 .  FIG. 4A  shows a graphical representation of an example of a plot  400  of voltage  402  (in millivolts) versus time  404  (in picoseconds) of the input split signals  324  and  326 . As an example, the first delayed split signal  324  may be shown in plot  400  as first signal plot  406  and the second delayed split signal  326  may be shown as second signal plot  408 . 
   Also shown in  FIG. 4A  is the time delay  440  (in picoseconds) between the first delayed split signal  324  and second delayed split signal  326 . During the duration of time delay  440 , there exists a difference in amplitude voltage  410  (in millivolts) between the first delayed split signal  324  and the second delayed split signal  326  as shown by the first signal plot  406  and the second signal plot  408 , respectively. 
     FIG. 4B  shows a graphical representation of an example of a plot  420  of voltage  422  versus time  424  of the output signals  426  and  428  (corresponding to first differential outputs  328  and  330 ) from the difference amplifier  306  shown in  FIG. 3 . The output signals  426  and  428  are the result of amplifying the amplitude difference  410 , which results in the output signals  426  and  428  having pulse widths  442  that correspond to the time delay difference  440 . 
   In this example, generally, a pulse  430  and an opposite-going pulse  432  will be generated as the first delayed split signal  324  and second delayed split signal  326  transition low and then high, respectively. The opposite-going pulse  432  may be suppressed by applying an optional DC offset  332  (through, for example, optional impedance  334 ) between the inputs of the difference amplifier  306  or by other means appreciated by those skilled in the art, such as, for example, a potentiometer connected to a voltage reference, a digitally-controlled voltage reference, or a current source connected to impedance  334 . 
     FIG. 5A  shows a graphical representation of a plot  500  of voltage  502  (in millivolts) versus time  504  (in picoseconds) of the input split signals  324  and  326  when the DC offset  332  is applied. The DC offset creates a voltage difference between the split signals  324  and  326 . An example of this voltage difference  510  is plotted along with the input signals  506  and  508 . 
   When this voltage difference  510  and the voltage difference  512  caused by the time delay is amplified by the difference amplifier  306  and the amplifier is limited in amplitude, the opposite-going pulses  432  and  442 ,  FIG. 4B , will be suppressed, and the resulting pulses will always go in the same direction.  FIG. 5B  shows a graphical representation of an example of a plot  520  of voltage  522  versus time  524  of the output signals  526  and  528  with opposite-going pulses suppressed. As in the previous example, the width  542  of the pulses corresponds to the time delay difference  540  between the input signals to the difference amplifier  306 . The width  542  also depends on the value of applied DC offset  332 ,  FIG. 3 , which provides a means of adjusting the width of the pulses when the input signals are not ideal square waves. 
   In  FIG. 6 , a block diagram of an example of another implementation of the SSPG  600  that includes an input amplifier  602  is shown. The input amplifier  602  may be a shaping amplifier that converts an arbitrary input signal  618  to an output signal  620  that more closely approximates a square wave. An example of the class of shaping amplifiers includes a limiting amplifier. Without an input shaping amplifier of sufficient gain, the characteristics of the output pulse train could vary with input drive level for input signals that do not approximate square waves. The addition of the input amplifier  602  allows the use of standard microwave sources, which generally only produce sinusoidal signals. 
   The SSPG  600  may include the input amplifier  602  and a splitter module  604 , delay module  606 , and difference amplifier  608 . In this implementation example, the input amplifier  602  is in signal communication with the splitter module  604  via signal path  610 . The splitter module  604  is in signal communication with the both the difference amplifier  608  and delay module  606  via signal paths  612  and  614 , respectively. The difference amplifier  608  is also in signal communication with the delay module  606  via signal path  616 . 
   In an example of operation, the SSPG  600  receives an input signal  618  at the input amplifier  602 , which shapes the input signal  618  and passes the shaped input signal  620  to the splitter module  604 . The splitter module  604  receives the shaped input signal  620  and in response splits the shaped input signal  620  to produce two split signals (first split signal  622  and second split signal  624 ) that are passed to difference amplifier  608  and delay module  606  via signal paths  612  and  614 , respectively. In response to receiving the second split signal  624 , the delay module  606  delays the second split signal  624  to produce a delayed split signal  626  that is passed to the difference amplifier  608  via signal path  616 . The difference amplifier  608  receives the first split signal  622  and the delayed split signal  626  and in response produces an output signal  628  that is proportional to the voltage difference between the first split signal  622  and delayed split signal  626 . 
   Similar to the example described in  FIG. 3 , an opposite-going pulse may also be generated as the first delayed split signal  622  and second delayed split signal  626  transition in the opposite direction. This opposite-going pulse may be suppressed by applying an optional DC offset (not shown) between the inputs of the difference amplifier  608  or by other means. 
   In  FIG. 7 , a block diagram of an example of yet another implementation of the SSPG  700  that includes a divider module  704  is shown. The divider module  704  reduces phase noise and jitter for the SSPG  700  and also shapes the input signal to more closely resemble a square wave. The SSPG  700  may also include a splitter module  706 , delay module  708 , and difference amplifier  710 . In this implementation example, the divider module  704  is in signal communication with splitter module  706  via signal path  714 . The splitter module  706  is in signal communication with the both the difference amplifier  710  and delay module  708  via signal paths  716  and  718 , respectively. The difference amplifier  710  is also in signal communication with the delay module  708  via signal path  720 . 
   In an example of operation, the SSPG  700  receives an input signal  722  at the divider module  704 , which produces a divided and shaped input signal  726 . The divider module  704  passes the divided input signal  726  to the splitter module  706 . The divider module  704  may be a device capable of lowering the repetition frequency of the input signal  722  by an integer value (i.e., a divide by 2, divide by 4, divide by 8, etc.) in such a manner as to reduce the phase noise and jitter of the amplified input signal  722  and produce a square wave output. Examples of devices that may be utilized as the divider module  704  include sequential logic circuits such as a static frequency divider, ripple counter or other similar type devices. The divider module  704  may include a trigger signal  736  that may be used as a reference to the decreased output repetition frequency of the divided input signal  726 . 
   The splitter module  706  receives the divided input signal  726  and in response splits the divided input signal  726  to produce two split signals (first split signal  728  and second split signal  730 ) that are passed to the difference amplifier  710  and delay module  708  via signal paths  716  and  718 , respectively. In response to receiving the second split signal  730 , the delay module  708  delays the second split signal  730  to produce a delayed split signal  732  that is passed to the difference amplifier  710  via signal path  720 . The difference amplifier  710  receives the first split signal  728  and the delayed split signal  732  and, in response, produces an output  734  that is proportional to the voltage difference between the first split signal  728  and delayed split signal  732 . 
   Again, similar to the example described in  FIG. 3 , an opposite-going pulse may also be generated as the first delayed split signal  728  and second delayed split signal  732  transition in the opposite direction. This opposite-going pulse may be suppressed by applying an optional DC offset (not shown) between the inputs of the difference amplifier  710 . 
   The divider module  704  may be replaced by a multiplier module (not shown) that increases the repetition frequency of input signal  724  by an integer value and also produces a square wave output. This may result in more energy per output tone (in the frequency domain) in output signal  734  and may also allow lower frequency input signals  722  to be used. 
   As an example of operation, in  FIG. 8 , a graphical representation of an example of a plot  800  of voltage  802  (in volts) versus time  804  (in nanoseconds) of a measurement of a negative pulse output  806  of the SSPG  200 ,  FIG. 2 , with a pulse width of about 35 picoseconds and the opposite-going pulse suppressed, is shown. 
   Additionally,  FIG. 9  shows a graphical representation of an example of a plot  900  of the amplitude  902  (in dBV) versus frequency  906  (in gigahertz) of a measurement of the amplitude spectrum  908  for the pulse  806  shown in  FIG. 8  with a repetition frequency of 10 MHz, and the phase  904  (in degrees) versus frequency  906  (in gigahertz) of a measurement of the phase spectrum  910  for the pulse  806  shown in  FIG. 8  with a repetition frequency of 10 MHz. 
     FIG. 10  shows a flow diagram  1000  of the steps performed in an example of a process of operation of the SSPG  200  shown in  FIG. 2 . The process begins in step  1002 , and in step  1004 , a splitter module of SSPG  200 ,  FIG. 2 , receives an input signal. In step  1006 , the splitter module splits the signal into two split signals, a first split signal and a second split signal. The second split signal is then time delayed, in step  1008 , to produce a delayed split signal that is input to the difference amplifier with the first split signal. In optional step  1010 , an optional DC offset is applied between the inputs of the difference amplifier, which amplifier amplifies the difference between the first split signal and the delayed split signal and limits the output amplitude, producing an output that is a pulse train with each pulse going in the same direction. The process then ends in step  1012 . 
   While the foregoing description refers to the use of an SSPG, the subject matter is not limited to such a system. Any signal generation instruments or systems that could benefit from the functionality provided by the components described above may be implemented in the SSPG. 
   Moreover, it will be understood that the foregoing description of numerous implementations has been presented for purposes of illustration and description. It is not exhaustive and does not limit the claimed inventions to the precise forms disclosed. Modifications and variations are possible in light of the above description or may be acquired from practicing the invention. The claims and their equivalents define the scope of the invention.

Technology Classification (CPC): 6