Patent Abstract:
A apparatus provides a voltage clamp step-up boost converter that is capable of reducing voltage stress on a switch and a diode of the boost converter without using a dissipative snubber and that is capable of reducing a switching loss while maintaining a high input-to-output boost ratio.

Full Description:
RELATED APPLICATIONS 
       [0001]    This application claims the benefit of Korean Patent Application No. 10-2013-0074203, filed on Jun. 27, 2013, which is hereby incorporated by reference as if fully set forth herein. 
       FIELD OF THE INVENTION 
       [0002]    The invention relates to a voltage clamp step-up boost converter, and more specifically, to a voltage clamp step-up boost converter that removes the configuration of a dissipative snubber using a resonant clamp capacitor. 
         [0003]    This work was supported by the MSIP (Ministry of Science, ICT and Future Planning) and NIPA (National IT Industry Promotion Agency) in Korea under Project 2013-H0301-13-2007 [Technology Research for Energy-IT Convergence]. 
       BACKGROUND OF THE INVENTION 
       [0004]    Recently, various power supply units used to boost a low DC voltage are being developed for electronic devices based on a fuel cell or battery. In particular, a boost converter using a tapped inductor is launched in the market in order to satisfy a high boost ratio, high power conversion efficiency, and low manufacturing cost. 
         [0005]    The boost converter using the tapped inductor is manufactured by adding the tapped inductor serving as a transformer to the boost converter. In connection with the boost converter using the tapped inductor, Korean Patent Publication No. 2010-0082084 A (laid-open published on Jul. 16, 2010) discloses a method of embodying a zero-voltage turn-on and zero-current turn-off function by using a tapped inductor of the boost converter. 
         [0006]    In the boost converter using tapped inductor, it is possible to obtain a high boost ratio, but an inductor and a capacitor of a switch causes an occurrence of resonance when the switch is turned off. As a result, a surge voltage is generated across the switch, which incurs an excessive stress on the switch. Hence, the boost converter using tapped inductor needs to use a high withstand voltage diode and a dissipative snubber. 
       SUMMARY OF THE INVENTION 
       [0007]    In view of the above, the present invention provides a voltage clamp step-up boost converter that is capable of reducing voltage stress on a switch and a diode of the boost converter without using a dissipative snubber and that is capable of reducing a switching loss while maintaining a high input-to-output boost ratio. However, the technical subject of the embodiment of the present invention is not limited to the foregoing technical subject, and there may be other technical subjects. 
         [0008]    In accordance with an aspect of the embodiment, there is provided an apparatus for a voltage clamp step-up boost converter comprising: a leakage inductor having a first end connected to a power supply unit; a tapped inductor having a first end connected to a second end of the leakage inductor; a magnetizing inductor having a first end connected to the second end of the leakage inductor and a second end connected to a second end of the tapped inductor; a switch having a first end connected to the second end of the tapped inductor and a second end connected to a second end of the power supply unit; a first diode having a first end connected to the second end of the tapped inductor; a second diode having a first end connected to a second end of the first diode and a second end connected to a third end of the tapped inductor; a resonant clamp capacitor having a second end connected between the second end of the first diode and the first end of the second diode and a first end connected between the first end of the power supply unit and the first end of the leakage inductor, the resonant clamp capacitor being configured to perform the clamping of the voltage across the switch and zero-voltage switching thereof when the switch is turned-off; an output capacitor having a first end connected to the second end of the second diode and a second end connected to the second end of the switch; an output load resistor having a first end connected to the first end of the second end of the output capacitor and a second end connected to the output capacitor; and a blocking capacitor having a first end connected to the third end of the tapped inductor and a second end connected to the second end of the second diode, wherein when the switch is turned-on, the voltage clamp step-up boost converter is configured to form a conductive path through the power supply unit, the resonant clamp capacitor, the blocking capacitor, the tapped inductor, and the switch and cause resonance through the resonant clamp capacitor and the leakage inductor with each other to decrease the voltage applied to the resonant clamp capacitor to a negative (−) voltage, thereby making the switch to be zero-current turned-on; and wherein when the switch is turned-off, the voltage clamp step-up boost converter is configured to form a conductive path through the leakage inductor, the tapped inductor, the first diode, and the resonant clamp capacitor to increase the voltage applied to the resonant clamp capacitor to a positive (+) voltage, thereby making the switch to be zero-voltage turned-off. 
         [0009]    In accordance with any one of solutions to the aforementioned subject of the present invention, it is possible to reduce the voltage stress on a switch and a diode of the boost converter without using a dissipative snubber and to reduce a switching loss while maintaining a high input-output boost ratio. 
     
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         [0010]    The above and other objects and features of the present invention will become apparent from the following description of the embodiments given in conjunction with the accompanying drawings, in which: 
           [0011]      FIG. 1  is a circuit diagram of a voltage clamp step-up boost converter in accordance with an embodiment of the present invention; 
           [0012]      FIGS. 2A to 2C  are circuit diagrams illustrating other embodiments of a voltage clamp step-up boost converter shown in  FIG. 1 ; 
           [0013]      FIGS. 3A to 3N  are circuit diagrams and timing diagrams of waveforms explaining the operation of the voltage clamp step-up boost converter shown in  FIG. 1 ; and 
           [0014]      FIGS. 4A and 4B  illustrates experimental waveforms of the voltage clamp step-up boost converter of  FIG. 1  and a prior art for the comparison between them. 
       
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
       [0015]    Hereinafter, embodiments of the present invention will be described in detail with reference to the accompanying drawings so that they can be readily implemented by those skilled in the art. However, the present invention may be embodied in different forms, but it is not limited thereto. In drawings, further, portions unrelated to the description of the present invention will be omitted for clarity of the description, and like reference numerals and like components refer to like elements throughout the detailed description. 
         [0016]    In the entire specification, when a portion is “connected” to another portion, it means that the portions are not only “connected directly” with each other but they are electrically connected” with each other by way of another device between them. Further, when a portion “comprises” a component, it means that the portion does not exclude another component but further comprises other component unless otherwise described. Furthermore, it should be understood that one or more other features or numerals, steps, operations, components, parts or their combinations can be or are not excluded beforehand. 
         [0017]    Hereinafter, the embodiments of the present invention will be described in detail with reference to the accompanying drawings. 
         [0018]      FIG. 1  is a circuit diagram of a voltage clamp step-up boost converter in accordance with an embodiment of the present invention, and  FIGS. 2A to 2C  are circuit diagrams illustrating other embodiments of the voltage clamp step-up boost converter shown in  FIG. 1 . 
         [0019]    Before describing the embodiment of the present invention, a voltage clamp step-up boost converter  1  shown in  FIG. 1  is defined functionally as follows. 
         [0020]    The voltage clamp step-up boost converter  1  may include a boost converter, a tapped inductor, a resonant clamp capacitor, a blocking capacitor, and an output load resistor. Herein, reference numerals would not be assigned to the respective components of the voltage clamp step-up boost converter  1  because of a mere functional definition of them. 
         [0021]    The boost converter serves to store current applied from a power supply unit in at least one inductor, add energy stored in the at least one inductor to the energy of the power supply voltage to deliver the added energy to an output end in accordance with on/off operations of a switch, and then output a boosted voltage through the output end. 
         [0022]    The tapped inductor outputs an increased voltage based on a conversion factor, and the blocking capacitor is charged with the voltage in accordance with the on/off operations of the switch. In addition, the boosted voltage is applied to the output load resistor in accordance with the outputs from the boost converter, the tapped inductor, and the blocking capacitor. In the aforementioned configuration, the output load resistor may be incorporated into the boost converter, however, for the sake of convenience of explanation, the description thereof will be made separately. 
         [0023]    Accordingly, the voltage clamp step-up boost converter  1  of the embodiment may have a high boost ratio by totaling all of the boost ratio of the boost converter itself, the boost ratio based on the turn ratio of the tapped inductor and the voltage charged in the blocking capacitor. 
         [0024]    Hereinafter, the connection of the components in the voltage clamp step-up boost converter will be described in detail. 
         [0025]    Referring to  FIG. 1 , the voltage clamp step-up boost converter  1  may include a power supply unit  100 , a leakage inductor  210 , a magnetizing inductor  230 , a tapped inductor  300 , a switch  400 , a first diode  510 , a second diode  520 , a resonant clamp capacitor  600 , an output capacitor  710 , an output load resistor  730 , a DC blocking capacitor  800 , and an output diode  900 . 
         [0026]    The leakage inductor  210  has a first end connected to the power supply unit  100  and a second end connected to the tapped inductor  300  and the magnetizing inductor  230 . The magnetizing inductor  230  has a first end connected to a second end of the leakage inductor  210  and a second end connected to a second end of the tapped inductor  300 . 
         [0027]    The tapped inductor  300  has a first end connected to the second end of the leakage inductor  210 , a second end connected to a first end of the switch  400 , and a third end connected to a first end of the blocking capacitor  800 . The tapped inductor  300  may have a conversion factor of 1:N, where the first end of the tapped inductor becomes the primary side and the third end thereof becomes the secondary side. Like a transformer, the input-to-output conversion ratio of the tapped inductor  300  may be determined based on a coupling coefficient. 
         [0028]    The switch  400  has the first end connected to the second end of the tapped inductor  300  and a second end connected to the second end of the power supply unit  100 . The switch  400  may be, for example, any one of a BJT (Bipolar Junction Transistor), a JFET (Junction Field-Effect Transistor), a MOSFET (Metal-Oxide Semiconductor Field-Effect Transistor), and a GaAs MESFET (Metal Semiconductor FET). 
         [0029]    The first diode  510  has a first end that is connected to the second end of the tapped inductor  300  and a second end that is connected to a second end of the resonant clamp capacitor  600  and a first end of the second diode  520 . Further, the second diode  520  has the first end connected to the second end of the first diode  510  and a second end connected to the third end of the tapped inductor  300 . 
         [0030]    The resonant clamp capacitor  600  has a second end connected between the second end of the first diode  510  and the first end of the second diode  520 . The resonant clamp capacitor  600  may be interposed for the voltage clamping across the switch  400  and the zero-voltage switching when the switch  400  is turned off. In this case, the first end of the resonant clamp capacitor  600  may be connected to a node to ensure that a constant voltage level is maintained. That is, the first end of the resonant clamp capacitor  600  is used as a clamp node, which may be connected to any node at which the constant voltage level is maintained. This will be explained with reference to  FIGS. 2A to 2C . 
         [0031]    Referring now to  FIG. 2A , a resonant clamp capacitor  600  has a second end that is fixed between a first diode  510  and a second diode  520 . The resonant clamp capacitor  600  also has a first end that is freely connected to any one of points A, B, and C. The embodiment shown in  FIG. 1  is defined as a case where the first end of the resonant clamp capacitor  600  is connected to a point A; an embodiment shown in  FIG. 2A  is defined as a case where the first end of the resonant clamp capacitor  600  is connected to a point B; and an embodiment shown in  FIG. 2C  is defined as a case where the first end of the resonant clamp capacitor  600  is connected to a point C. 
         [0032]    When the first end of the resonant clamp capacitor  600  is connected to the point A, the arrangement corresponds to that illustrated in  FIG. 1 . In this case, the first end of the resonant clamp capacitor  600  is connected between the first end of the power supply unit  100  and the first end of the leakage inductor  210 . When the first end of the resonant clamp capacitor  600  is connected to the point B, the arrangement corresponds to that illustrated in  FIG. 2B . In this case, the first end of a resonant clamp capacitor  600  is connected between the second end of a power supply unit  100  and the second end of a switch  400 . When the first end of the resonant clamp capacitor  600  is connected to the point C, the arrangement corresponds to that illustrated in  FIG. 2C . In this case, the first end of the resonant clamp capacitor  600  is connected between the second end of an output diode  900  and the first end of an output capacitor  710 . 
         [0033]    The overall operations of the voltage clamp step-up boost converters illustrated in  FIGS. 2A to 2C  are substantially same one other, except the difference in the offset voltages applied to the resonant clamp capacitor  600 . Specifically, the offset voltage applied to the resonant clamp capacitor  600  of  FIG. 2A  may be lower than that of the resonant clamp capacitor  600  of  FIGS. 2B and 2C . Therefore, the voltage clamp step-up boost converter  1  of the embodiment illustrated in  FIG. 2A  may exhibit the lowest withstand voltage property. 
         [0034]    Referring back to  FIG. 1 , the output capacitor  710  has a first end connected to the second end of the second diode  520  and a second end connected to the second end of the switch  400 . In addition, the output load resistor  730  has a first end connected to the first end of the output capacitor  710  and a second end connected to the second end of the output capacitor  710 . 
         [0035]    The DC blocking capacitor  800  has a first end connected to the third end of the tapped inductor  300  and a second end connected to the second end of the second diode  520 . The output diode  900  has a first end connected to the second ends of the blocking capacitor  800  and the second diode  520  and a second end connected to the first end of the output capacitor  710 . 
         [0036]      FIGS. 3A to 3N  illustrate circuit diagrams and timing diagrams of waveforms explaining the operation of the voltage clamp step-up boost converter shown in  FIG. 1 . Hereinafter, the operation of the voltage clamp step-up boost converter  1  having the foregoing configuration will be explained in detail with reference to  FIG. 1  and  FIGS. 3A to 3N . 
         [0037]    Before explaining the operation, it is assumed for the convenience of the interpretation of the operation modes as follows: 
         [0038]    i) the magnetizing inductor  230  has inductance as large as to ignore a current ripple caused by the magnetizing inductor  230 ; ii) the components of the voltage clamp step-up boost converter  1  of the embodiments are ideal; iii) the output capacitor  710  has capacitance as large as to ignore the voltage ripple of an output voltage Vo; iv) the blocking capacitor  800  has capacitance as large as to ignore the voltage ripple of a voltage V C  applied to the blocking capacitor  800 ; and V) all operations are in steady-states. 
         [0039]    Hereinafter, two terms in pairs will be designated as the same component such as the power supply unit  100  and V in ; the leakage inductor  210  and L Lk ; the magnetizing inductor  230  and L m ; the switch  400  and M; the first diode  510  and D 1 ; the second diode  520  and D 2 ; the resonant clamp capacitor  600  and C S ; the output capacitor  710  and C O ; the output load resistor  730  and R O ; the blocking capacitor  800  and C C ; and the output diode  900  and D 3 . Moreover, i pri  means the primary side current of the tapped inductor  300 ; V LK  means the voltage applied to the leakage inductor  210 ; V Lm  means the voltage applied to the magnetizing inductor  230 ; i ds  means current flowing to a drain and source of the switch  400 ; V sec  means the secondary side voltage of the tapped inductor  300 ; V C  means the voltage applied to the blocking capacitor  800 ; i sec  means the secondary side current of the tapped inductor  300  (the waveform of i sec  will be represented in an inverted form throughout  FIGS. 3A to 3N  for the sake of convenience); V D1  the voltage applied to the first diode  510 ; in means the current flowing to the first diode  510 ; V S  means the voltage applied to the resonant clamp capacitor  600 ; i CS  means the current flowing to the resonant clamp capacitor  600 ; V D2  means the voltage applied to the second diode  520 ; i D2  means the current flowing to the second diode  520 ; V D3  means the voltage applied to the output diode  900 ; and i D3  means the current flowing to the output diode  900 . 
         [0040]      FIG. 3A  represents a conductive path in accordance with the operation of the voltage clamp step-up boost converter at t 0 ˜t 1 . Referring to  FIG. 3B , the switch  400  is in a turned-off state prior to t 0 , and the energy stored in the magnetizing inductor  230  is passed to the output end through the output diode  900 . At t 0 ˜t 1 , the switch  400  become a turned-on state, a conductive path of the voltage clamp step-up boost converter is illustrated as in  FIG. 3A . 
         [0041]    As illustrated in the  FIG. 3B , the voltage V ds  across the switch  400  rapidly decreases from V O /(1+N) to 0V and at the same time the primary side current i pri  of the tapped inductor  300  increases and the secondary side current i sec  decreases (in view of its inverted waveform). Specifically, the secondary side current i sec  slowly decreases to 0 A by the leakage inductor  210  (in view of its inverted waveform) and the magnetizing inductor  230  and the primary side current i pri  slowly increases. 
         [0042]    Therefore, because the current i pri −i sec  which flows through the switch  400  gradually increases, when the switch  400  is turned on, the voltage V ds  and the current i ds  have a phase reversal relation enough not to overlap with each other in their waveforms, thereby reducing the switching loss. 
         [0043]      FIG. 3C  represents a conductive path in accordance with the operation of the voltage clamp step-up boost converter at t 1 ˜t 2 . Referring to  FIG. 3D , the operation of the voltage clamp step-up boost converter at t 1 ˜t 2  is started when the primary side current i pri  gradually increases to become equal to the current i Lm  of the magnetizing inductor  230  and the secondary side current i sec  of the magnetizing inductor  230  becomes equal to 0 A. At this time, the output diode  900  is turned off and the second diode  520  is turned on, thereby forming the conductive path illustrated in  FIG. 3C . Accordingly, the voltage applied to the blocking capacitor  800  becomes to reduce to −V in  due to the resonance of the resonant clamp capacitor  600  and the leakage inductor  210 . 
         [0044]      FIG. 3E  represents a conductive path in accordance with the operation of the voltage clamp step-up boost converter at t 2 ˜t 3 . Referring to  FIG. 3F , the operation of the voltage clamp step-up boost converter at t 2 ˜t 3  is started when the voltage applied to the resonant clamp capacitor  600  reaches −V in . At this time, the first diode  510  is conducted, thereby forming the conductive path illustrated in  FIG. 3E . In this case, because the switch  400  is in a turned-on state, the input voltage V in  is applied to both of the leakage inductor  210  and the magnetizing inductor  230 . Accordingly, energy is stored in the magnetizing inductor  230  and simultaneously, NV in  is charged in the blocking capacitor  800  with the turn ratio of the tapped inductor  300 . 
         [0045]      FIG. 3G  represents a conductive path in accordance with the operation of the voltage clamp step-up boost converter at t 3 ˜t 4 . Referring to  FIG. 3H , when the blocking capacitor  800  is fully charged, the first diode  510  and the second diode  520  are turned off as illustrated in  FIG. 3G . Since the switch  400  is still turned on, the input voltage V in  is applied to the leakage inductor  210  and the magnetizing inductor  230  as similar to  FIG. 3C  and thus energy is stored in the magnetizing inductor  230 . 
         [0046]      FIG. 3I  represents a conductive path in accordance with the operation of the voltage clamp step-up boost converter at t 4 ˜t 5 . Referring to  FIG. 3I , when the switch  400  is turned off, the conductive path is formed as illustrated in  FIG. 3I  and the current i Lm  of the switch  400  is rapidly reduced to 0 A as illustrated in  FIG. 3J . At the same time, the energy stored in the leakage inductor  210  and the magnetizing inductor  230  is charged in the resonant clamp capacitor  600  through the first diode  510 . Therefore, the voltage applied to the resonant clamp capacitor  600  begins to gradually increase from −V in . Further, the voltage across the switch  400 , which is represented as V in +V CS , gradually begins to increase from 0V. Accordingly, when the switch  400  is turned-off, the voltage V ds  and the current i ds  have a phase reversal relationship enough not to overlap with each other in their waveforms, whereby it is possible to reduce the switching loss. 
         [0047]      FIG. 3K  represents a conductive path in accordance with the operation of the voltage clamp step-up boost converter at t 5 ˜t 6 . Referring to  FIG. 3L , when the voltage V ds  across the switch  400  reaches V O /(1+N), the output diode  900  is conducted and the resonant clamp capacitor  600  and the leakage inductor  210  cause resonance together. Therefore, the voltage V S  of the resonant clamp capacitor  600  and the voltage V ds  of the switch  400  increase as illustrated in Fig. L, and the current i D1  of the first diode  510  becomes 0 after ¼ resonance cycle. Simultaneously, when the secondary side current i sec  reaches i Lm /(N+1), the operation at the t 5 ˜t 6  is finished. 
         [0048]      FIG. 3M  represents a conductive path in accordance with the operation of the voltage clamp step-up boost converter at t 6 ˜t 7 . Referring to  FIG. 3N , when the secondary side current i sec  reaches the i Lm /(N+1), the conductive path is formed as illustrated in  FIG. 3M  and the energy stored in the leakage inductor  210  and the magnetizing inductor  230  is passed to the output end. Thereafter, when the switch  400  is again turned on, the operation at t 6 ˜t 7  is finished. 
         [0049]    The voltage relational expressions are derived in accordance with the aforementioned operations as follows. 
         [0050]    First, let the operations at t 0 ˜t 2  and t 4 ˜t 6  be ignored for the convenience of deriving the voltage relational expressions related to the respective components off the voltage clamp step-up boost converter in accordance with the embodiment of the present invention. 
         [0051]    The voltage V C  is applied to the secondary side of the tapped inductor  300  for the duration DT S  where the switch  400  is in a turned-on state whereas the voltage −(V O −V C −V in )N/(N+1) is applied to the secondary side of the tapped inductor  300  for the duration (1−D)T S  where the switch  400  is in a turned-off state. Therefore, the following Equation can be derived by applying a voltage-time balanced condition to the secondary side of the tapped inductor  300 . 
         [0000]    
       
         
           
             
               
                 
                   
                     
                       DT 
                       S 
                     
                      
                     
                       V 
                       C 
                     
                   
                   = 
                   
                     
                       ( 
                       
                         1 
                         - 
                         D 
                       
                       ) 
                     
                      
                     
                       T 
                       S 
                     
                      
                     
                       N 
                       
                         N 
                         + 
                         1 
                       
                     
                      
                     
                       ( 
                       
                         Vo 
                         - 
                         
                           V 
                           C 
                         
                         - 
                         
                           V 
                           in 
                         
                       
                       ) 
                     
                   
                 
               
               
                 
                   [ 
                   
                     EQUATION 
                      
                     
                         
                     
                      
                     1 
                   
                   ] 
                 
               
             
           
         
       
     
         [0052]    By rearranging the Equation 1, V C  can be expressed as the following Equation 2. 
         [0000]        V   C   NV   in   [EQUATION 2]
 
         [0053]    In the meantime, the voltage V in  is applied to an voltage V LM  of the primary side of the magnetizing inductor  230  for the duration DT S  where the switch  400  is in a turned-on state whereas the voltage −(V O −V in −V C )/(1+N) is applied to the voltage V LM  of the primary side of the magnetizing inductor  230  for the duration (1-D)T S  where the switch  400  is in a turned-off state. Therefore, the following Equation can be derived by applying voltage-time balanced condition to the primary side of the tapped inductor  300 . 
         [0000]        DT   S   V   in =(1− D ) T   S ( V   O   −V   in   −V   C )/(1+ N )  [EQUATION 3]
 
         [0054]    By substituting the Equation 3 with the Equation 2, the following Equation 4 can be derived. 
         [0000]    
       
         
           
             
               
                 
                   
                     V 
                     O 
                   
                   = 
                   
                     
                       
                         N 
                         + 
                         1 
                       
                       
                         1 
                         - 
                         D 
                       
                     
                      
                     
                       V 
                       in 
                     
                   
                 
               
               
                 
                   [ 
                   
                     EQUATION 
                      
                     
                         
                     
                      
                     4 
                   
                   ] 
                 
               
             
           
         
       
     
         [0000]    where V O  represents an output voltage, V in  represents an input voltage, N represents the conversion factor (or, turn ratio) of the tapped inductor, and D represents a duty ratio. 
         [0055]      FIGS. 4A and 4B  shows experimental waveforms of the voltage clamp step-up boost converter of  FIG. 1  and a prior art for the comparison between them. Specifically,  FIG. 4A  shows an experimental result on the voltage clamp step-up boost converter of the present invention using a simulation tool. 
         [0056]    The specification used in the simulation is as follows: the input voltage is 24V; the output voltage and electricity are 250V and 100 W, respectively; the inductance of the leakage inductor  210  is 10 μl; the inductance of the magnetizing inductor  230  is 100 μH; the turn ratio of the inductors is 1:4; and the capacitance of the resonant clamp capacitor  600  is 47 nF. 
         [0057]    Referring to  FIG. 4A , it can be known that regardless of the resonance caused by the inductor component of the tapped inductor and the parasitic capacitor, the voltage of each component is clamped by the input and output voltages. Further, the current of the switch  400  increases with a slow inclination when the switch  400  is turned on. Therefore, the waveforms of the voltage V ds  across the switch  400  and the current i ds  of the switch  400  are not overlap with each other. Meanwhile, the voltage of the switch  400  also increases with a slow inclination when the switch  400  is turned off. Therefore, the waveforms of the voltage V ds  across the switch  400  and the current I ds  of the switch  400  are also not overlap. Consequently, a very low switching loss is achieved in the actual implementation. 
         [0058]    On the other hand,  FIG. 4B  shows an experimental result on the voltage clamp step-up boost converter of the prior art under the same condition. It can be seen from  FIG. 4B  that the diode and switch have high voltage stress with the resonance of the inductor component of the transformer and the parasitic capacitor. Particularly, it is observed that the magnitude of current of the magnetizing inductor in the tapped inductor is 7.5 A which is higher than the embodiment of the present invention with respect to the same output load. In addition, the prior art requires the winding number more than usual and a magnetic core having a large air gap and large size in order to prevent the saturation of the tapped inductor. 
         [0059]    As set forth above, the voltage clamp step-up boost converter in accordance with the embodiments can be ensured to get the input-to-output boost ratio which is higher than the conventional tapped inductor boost converter by combining all of the turn ratio of the transformer, the voltage of the blocking capacitor, and the boost ratio of the boost converter itself. Especially, the voltage clamp step-up boost converter enables to make the zero current switching by means of the leakage inductance when switch is in a turned-on state and to make the zero-voltage switching by means of the resonant clamp capacitor when the switch is in a turned-off state, thereby significantly reducing the switching loss. Accordingly, the voltage clamp step-up boost converter of the embodiments enables to improve the system efficiency and heat generation. 
         [0060]    Description of the present invention as mentioned above is intended for illustrative purposes, and it will be understood to those having ordinary skill in the art that this invention can be easily modified into other specific forms without changing the technical idea and the essential characteristics of the present invention. Accordingly, it should be understood that the embodiments described above are exemplary in all respects and not limited thereto. For example, respective components described to be one body may be implemented separately from one another, and likewise components described separately from one another may be implemented in an integrated type. 
         [0061]    The scope of the present invention is represented by the claims described below rather than the foregoing detailed description, and it should be construed that all modifications or changes derived from the meaning and scope of the claims and their equivalent concepts are intended to be fallen within the scope of the present invention.

Technology Classification (CPC): 8