Patent Abstract:
Circuits, methods, and apparatus for transferring data from a device&#39;s input clock domain to a core clock domain. One example achieves this by using a retiming element between input and core circuits. The retiming element is calibrated by incrementally sweeping a delay and receiving data at each increment. Minimum and maximum delays where data is received without errors are averaged. This average can then be used to adjust the timing of a circuit element inserted in an input path between an input register clocked by an input strobe signal and an output register clocked by a core clock signal. In one example, an input signal may be delayed by an amount corresponding to the delay setting. In other examples, each input signal is registered using an intermediate register between the input register and the output register, where a clock signal is delayed by an amount corresponding to the delay setting.

Full Description:
CROSS-REFERENCES TO RELATED APPLICATIONS 
   This application claims the benefit of U.S. provisional application No. 60/857,249, filed Nov. 6, 2006, which is incorporated by reference. 

   BACKGROUND 
   The amount of data transferred between devices in computer systems has been increasing at a tremendous pace that shows no signs of abating. In particular, the amount of data transferred between memory devices and other devices, such as devices implemented using field programmable gate arrays (FPGAs), has grown prodigiously. Unfortunately, the rate at which these devices can process data has increased faster than the memory device&#39;s capacity to provide it. For this reason, faster memory interface protocols are being developed. 
   One such faster protocol is the Double-Data Rate 3 (DDR3) interface standard. In this standard, several memory devices communicate with a memory interface circuit on an FPGA or other device. Each memory device communicates using a number of data or DQ signals and a strobe or DQS signal. While the FPGA receives data, the FPGA provides a system clock signal to the memory devices, each of which provide a DQS and a number of DQ signals to the memory interface circuit. The memory devices use the system clock to adjust the frequency of the DQS and DQ signals. However, the system clock is routed to the memory devices using a fly-by topology. Accordingly, the DQ and DQS signals are provided asynchronously to the memory interface, that is, each memory device may provide DQS and DQ signals having any phase relationship to the system clock. 
   The DQ signals received by the memory interface are retimed using a phase-shifted version of the corresponding DQS signals. These retimed signals need to be retimed once again to an internal clock, which may be the system clock or a second clock signal, to transfer the signals to the core of the device. Unfortunately, if the timing between the phase-shifted DQS signal and the system clock is not optimal, data recovery errors may result. Conventional techniques have included using first-in-first-out memories, but these are comparatively large, complex circuits. 
   Thus, what is needed are circuits, methods, and apparatus that provide for the efficient transfer of data from a device&#39;s inputs to its core circuitry. 
   SUMMARY 
   Accordingly, embodiments of the present invention provide circuits, methods, and apparatus that provide for the transfer of data from an input clock domain to a device&#39;s core clock domain. An exemplary embodiment of the present invention achieves this by using a leveling element between a device&#39;s input and core circuits. One embodiment calibrates the leveling element by incrementally sweeping a delay and receiving data at each increment. Minimum and maximum delays where data is received without errors are recorded and averaged to generate a delay setting. This delay can then be used to adjust the leveling element inserted in an input path between an input register that is clocked by an input strobe signal and an output register that is clocked by a core clock signal. In various embodiments of the present invention, the delay may be used directly, that is, an input signal may be delayed by an amount corresponding to the delay setting. In other embodiments of the present invention, the leveling element is an intermediate register placed between the input register and the output register, where each input signal is retimed using an intermediate register, and where a clock signal for the intermediate register is delayed by an amount corresponding to the delay setting. In one such embodiment of the present invention, a number of clocks are provided to the intermediate registers, each to one group of data inputs, where the delay or phase of each clock signal is independently adjusted. In another embodiment of the present invention, a number of clocks are provided to each group of data inputs, where one of the number of clocks is selected and used to clock the intermediate registers in the group. In other embodiments of the present invention, other circuits, such as latches, may be used as the leveling element. 
   Another exemplary embodiment of the present invention provides a memory interface circuit that interfaces with a plurality of memory devices arranged, for example, on a dual inline memory module (DIMM). Each memory device communicates with the memory interface circuit using a strobe signal, referred to as a DQS signal, and several data lines, which are referred to as DQ signals. The memory interface provides a system clock to each of the memory devices. The memory devices use the system clock such that the DQS and DQ signals have the correct fundamental frequency and the strobe and data signals provided by each memory device are aligned with each other. However, newer memory interface standards, such as DDR3 route the system clock using a fly-by topology. This topology results in the reception of the system clock by the memory devices at different times. Accordingly, the memory devices each provide DQ and DQS signals at times that are skewed relative to each other. As a result, the received DQS strobe signals are out of phase with the system clock. 
   The memory interface receives data signals from the memory devices and retimes them using an input register clocked by a corresponding strobe signal. However, since the strobe signal is out of phase with the system clock in the memory controller, the input data signals are re-registered using an output register clocked by the system clock, or a second clock derived from the system clock for use by core circuitry connected to the memory interface. Unfortunately, if the strobe signal is improperly aligned with the system clock, data may not transfer from the input register to the output register properly, and errors in data reception may occur. 
   Accordingly, a specific embodiment of the present invention provides leveling elements implemented as delay elements between the input and output registers such that data is properly transferred to the core circuitry. To calibrate the delay elements, the delay provided by the delay element is incremented over a range of values. In this specific embodiment, the range of values is approximately covers one clock cycle period, though in other embodiments, the range of values may be greater or less than one clock cycle. At each increment, a known data pattern is provided by each memory device to the memory interface. The received data is checked for errors for each DQ signal in a group. Minimum and maximum delays where error-free reception occurs for the DQ signals in the group are noted. These delays may be averaged and the average delay used to delay the input signal. Each DQ/DQS group typically is delayed an independently determined delay, though each DQ signal in the group is typically delayed the same amount. In other embodiments, each DQ in a DQ/DQS group may be delayed an independent amount. 
   Another embodiment of the present invention provides leveling elements implemented as an intermediate register between the input and output registers. The intermediate register is clocked by a delayed version of the system clock, where the delay is calibrated for error-free data reception. In this embodiment, a phase-locked loop (PLL) generates the system clock and several delayed versions of the system clock. Each of the delayed versions of the system clock is provided to the intermediate registers for one group of DQ inputs. Again, the delays of these versions of the system clock are incrementally increased (or decreased) and a known data pattern is received at each increment. For each DQ group, minimum and maximum delays where error-free reception occurs for the DQ signals in the group are averaged and a clock delayed by this amount provided to intermediate registers for the DQ group. Typically, one clock line having one delay is used for each intermediate register in a DQ group, while each DQ group has a different delayed clock that has an independently calibrated delay. 
   Another embodiment of the present invention also provides leveling elements implemented as intermediate registers between the input and output registers. These intermediate registers are clocked by a delayed version of the system clock, where the delay is calibrated for error-free data reception. In this embodiment, a number of delay elements are used to generate a number of delayed clocks, which are in turn multiplexed using a clock multiplexer. Specifically, one clock, such as the synchronization clock that clocks the output synchronization registers or a second clock derived from the system clock, is received by the number of delay elements that generate a number of delayed clock signals. The delayed clock signals are routed to each DQ group. A clock multiplexer is associated with each DQ group, where the clock multiplexer selects one of the delayed clock signals and provides it to the intermediate registers in the DQ group. During calibration, the clock multiplexer incrementally adjusts the delay of its output clock signal by selecting different input clock signals. Again, a known data pattern is received at each increment. For each DQ group, minimum and maximum delays where error-free reception occurs for the DQ signals in the group are averaged and a clock delayed by this amount is selected by the clock multiplexer and provided to intermediate registers for the DQ group. Typically, the selected multiplexer input is chosen independently for each DQ group. 
   Various embodiments of the present invention may incorporate one or more of these or the other features described herein. A better understanding of the nature and advantages of the present invention may be gained with reference to the following detailed description and the accompanying drawings. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
       FIG. 1  is a simplified block diagram of a programmable logic device that is improved by incorporating embodiments of the present invention; 
       FIG. 2  is a block diagram of an electronic system that is improved by incorporating embodiments of the present invention; 
       FIG. 3  is a block diagram of a memory interface that is improved by the incorporation of embodiments of the present invention; 
       FIG. 4  is a block diagram illustrating a portion of the memory interface of  FIG. 3  in greater detail; 
       FIG. 5  is a simplified block diagram of a portion of an input path of a memory interface that is improved by the incorporation of an embodiment of the present invention; 
       FIG. 6  illustrates a possible timing for the circuitry of  FIG. 5  that may lead to metastates and other instabilities during data reception; 
       FIG. 7  is a block diagram illustrating a portion of a memory interface circuit that includes a leveling element consistent with an embodiment of the present invention; 
       FIG. 8  illustrates the timing of the circuitry shown in  FIG. 7 ; 
       FIG. 9  is a block diagram of a portion of a memory interface where a leveling element is implemented as a delay line according to an embodiment of the present invention; 
       FIG. 10  illustrates a delay line that may be used as the delay lines  940  and  942  in  FIG. 9  or other embodiments of the present invention; 
       FIG. 11  is a flowchart illustrating the calibration routine for setting a delay through the delays  940  and  942  in  FIG. 9 ; 
       FIG. 12  is a block diagram of a portion of a memory interface consistent with an embodiment of the present invention where the leveling element is a register; 
       FIG. 13  is a flowchart illustrating a method of adjusting a phase of a leveling clock according to an embodiment of the present invention; 
       FIG. 14  is a block diagram of a portion of a memory interface circuit according to an embodiment of the present invention; 
       FIG. 15  is a flowchart illustrating the operation of calibration logic employed by an embodiment of the present invention; 
       FIG. 16  is a block diagram of a delay-locked loop, a delay element, a number of delay elements, and a clock multiplexer that may be used to implement the delay-locked loop  1460 , delay  1420 , and delays  1440  in  FIG. 14 , or in other embodiments of the present invention; and 
       FIG. 17  illustrates one possible simplification of the circuitry of  FIG. 16 . 
   

   DESCRIPTION OF EXEMPLARY EMBODIMENTS 
     FIG. 1  is a simplified partial block diagram of an exemplary high-density programmable logic device or FPGA  100  wherein techniques according to the present invention can be utilized. PLD  100  includes a two-dimensional array of programmable logic array blocks (or LABs)  102  that are interconnected by a network of column and row interconnections of varying length and speed. LABs  102  include multiple (e.g., 10) logic elements (or LEs), an LE being a small unit of logic that provides for efficient implementation of user defined logic functions. 
   PLD  100  also includes a distributed memory structure including RAM blocks of varying sizes provided throughout the array. The RAM blocks include, for example, 512 bit blocks  104 , 4 K blocks  106 , and an M-Block  108  providing 512 bits of RAM. These memory blocks may also include shift registers and FIFO buffers. PLD  100  further includes digital signal processing (DSP) blocks  110  that can implement, for example, multipliers with addition or subtraction features. 
   It is to be understood that PLD  100  is described herein for illustrative purposes only and that the present invention can be implemented in many different types of PLDs, FPGAs, and the other types of digital integrated circuits. 
   While PLDs or FPGAs of the type shown in  FIG. 1  provide many of the resources required to implement system level solutions, the present invention can also benefit systems wherein a PLD is one of several components. 
     FIG. 2  shows a block diagram of an exemplary digital system  200 , within which the present invention may be embodied. System  200  can be a programmed digital computer system, digital signal processing system, specialized digital switching network, or other processing system. Moreover, such systems may be designed for a wide variety of applications, such as telecommunications systems, automotive systems, control systems, consumer electronics, personal computers, Internet communications and networking, and others. Further, system  200  may be provided on a single board, on multiple boards, or within multiple enclosures. 
   System  200  includes a processing unit  202 , a memory unit  204  and an input/output unit  206  interconnected together by one or more buses. According to this exemplary embodiment, a programmable logic device (PLD)  208  is embedded in processing unit  202 . PLD  208  may serve many different purposes within the system in  FIG. 2 . PLD  208  can, for example, be a logical building block of processing unit  202 , supporting its internal and external operations. PLD  208  is programmed to implement the logical functions necessary to carry on its particular role in system operation. PLD  208  may be specially coupled to memory  204  through connection  210  and to input/output unit  206  through connection  212 . 
   Processing unit  202  may direct data to an appropriate system component for processing or storage, execute a program stored in memory  204 , or receive and transmit data via input/output unit  206 , or other similar function. Processing unit  202  can be a central processing unit (CPU), microprocessor, floating point coprocessor, graphics coprocessor, hardware controller, microcontroller, programmable logic device programmed for use as a controller, network controller, and the like. Furthermore, in many embodiments, there is often no need for a CPU. 
   For example, instead of a CPU, one or more PLDs  208  can control the logical operations of the system. In an embodiment, PLD  208  acts as a reconfigurable processor, which can be reprogrammed as needed to handle a particular computing task. Alternately, programmable logic device  208  may itself include an embedded microprocessor. Memory unit  204  may be a random access memory (RAM), read only memory (ROM), fixed or flexible disk media, PC card flash disk memory, tape, or any other storage means, or any combination of these storage means. 
     FIG. 3  is a block diagram of a memory interface that is improved by the incorporation of embodiments of the present invention. This figure includes a number of memories, in this example arranged in a dual in-line memory module (DIMM)  300 , and an integrated circuit, in this example an FPGA  340 . The DIMM  300  includes a number of memory devices  310 ,  320 , through  330 . The FPGA  340  includes a memory controller  350  and core circuitry  360 . The memory controller  350  reads and writes data using a number of DQS/DQ groups  312 ,  322 , and  332 , and receives data from and provides data to the core circuits  360 . Timing for the DQS and DQ signals is derived from a system clock  352 , which is provided from the memory controller  350  to the memory devices  310 ,  320 , and  330 . 
   In DDR3 systems, the system clock  352  is routed using a fly-by topology. That is, the memory devices  310  through  330  receive the system clock  352  in a serial fashion. Other signals, such as control signals (not shown) may also be routed this way. This topology provides a greater signal integrity as compared to more conventional routing. The result of using this topology is that memory device  310  receives the system clock  352  first, and the other memory devices receive the system clock some time later, with memory device  330  receiving it last. The skew between the arrival of the system clock  352  at the memory devices can be on the order of a clock cycle. Since the timing for the DQ and DQS signals provided by the memory devices is based on the system clock  352 , the DQ and DQS signals received by the memory controller  350  may also be skewed by as much as a clock cycle. 
   Accordingly, the DDQS and DQ signal groups from the memory devices each operate at the same frequency but have phase relationships that are uncorrelated to each other. Without more, these phase shifts may lead to errors in the reception of data by the memory controller  350  due to timing errors that occur during the transfer of data from the capture registers to the synchronization registers, as shown below. Accordingly, embodiments of the present invention provide circuits, methods, and apparatus that provide for consistent and accurate data reception by memory controllers, such as the memory controller  350 . 
     FIG. 4  is a block diagram illustrating a portion of the memory interface of  FIG. 3  in greater detail. This figure includes a memory device  400  that further includes a memory core  402 , multipurpose registers  404 , and a memory input and output interface  406 , as well as an integrated circuit  460 , such as an FPGA, which includes a delay element  410 , capture registers  420  through  424 , synchronizing registers  430  through  434 , phase-locked loop  440 , and core circuits  450 . 
   In this example embodiment, a phase-locked loop  440  provides a system clock to the memory device  400 . The memory device in turn provides a data strobe DQS signal and data signals DQ 1 , DQ 2 , and DQN. The data strobe signal is phase shifted by delay circuit  410  to produce a delayed DQS signal, DDQS. The delayed strobe signaled DDQS clocks capture registers  420 ,  422 , and  424 , which capture input data signals DQ 1 , DQ 2 , and DQN, respectively. The outputs of the capture registers are provided to synchronization registers  430 ,  432 , and  434 , which are clocked by the system clock. The outputs the synchronization registers are provided to core circuits  450 . 
   In a typical system, the data strobe signal DQS is aligned with the data signals DQ 1 , DQ 2 , and DQN when provided by the memory interface  406 . Once received by the FPGA  460 , the DQS signal is delayed, typically by approximately 90 degrees (though other phase shifts may be required), so that the edges of the delayed DQS signal DDQS are centered to the bits of the incoming DQ data. This enables the capture registers to clock the incoming DQ data. 
   Again, the DQS signal may have any phase relationship with the system clock. Thus, the DDQS signal may also have any possible phase relationship with the system clock. This means that as data is passed from a capture register to a synchronization register, metastates or other instabilities may occur. This is shown further in the following figures. 
     FIG. 5  is a simplified block diagram of a portion of an input path of a memory interface that is improved by the incorporation of an embodiment of the present invention. This figure includes a delay element  510 , capture register  520 , and synchronization register  530 . Data is received on the DQ line by capture register  520 . The DQS signal is received from the memory devices and delayed or phase shifted by delay circuit  510  to generate a delayed DQS signal DDQS. The DDQS signal clocks the capture register, which provides a retimed data output CQ to the synchronization register  530 . The synchronization register  530  is clocked by the synchronization clock, and provides an output DATAOUT to core or other circuits. 
   If data transitions of the signal CQ occur near active edges of the system clock, metastates or other instabilities in the synchronization register may occur, leading to errors in the received data at DATAOUT. In the following examples, the active edges of the synchronization register  530  are shown as rising edges, though in other embodiments of the present invention, the active edges of the synchronization register  530  may be falling edges. 
     FIG. 6  illustrates a possible timing for the circuitry of  FIG. 5  that may lead to metastates and other instabilities during data reception. These metastates or other instabilities typically lead to errors in data reception. In this example, the timing diagram illustrates timing for a data signal DQ  610 , data strobe signal DQS  620 , delayed DQS signal DDQS  630 , retimed data signal CQ  640 , synchronization clock SYNC CLOCK  650 , and data output signal DATAOUT  660 . 
   Signals DQ  610  and DQS  620  are received from a memory device by an integrated circuit, such as an FPGA. The data strobe signal DQS  620  is phase shifted an amount  632  to generate DDQS  630 . DDQS  630  clocks the DQ  610  signal to generate CQ  640 . Edges of CQ  640  follow DQS rising edges by a clock-to-Q delay  642 . Again, the SYNC CLOCK  650  may have any timing relationship to DDQS  630 . If rising edges of the SYNC CLOCK  650  approach the data edges  644  by an amount less than the setup time  652 , metastates or data instabilities may occur. Similarly, if rising edges of SYNC CLOCK  650  are near data edge  646 , hold time  656  may be violated. If one of these conditions occurs, that is, the setup time  652  or the hold time  656  are violated, instabilities in the output signal DATAOUT  660  may occur. Accordingly, embodiments of the present invention provide leveling elements such that the signal CQ  640  maintains a relationship with the SYNC CLOCK  650  such that these registers do not become metastable and that instabilities do not occur. Examples are shown in the following figures. 
     FIG. 7  is a block diagram illustrating a portion of a memory interface circuit that includes a leveling element consistent with an embodiment of the present invention. This figure includes a capture register  720 , leveling element  725 , synchronization register  730 , delay  710 , delay-locked loop  740 , and phase-locked loop  750 . Data signal DQ is received by the capture register  720 . A data strobe signal DQS is received by the delay  710  and phase shifted to generate a delayed DQS signal DDQS that clocks the capture registers  720 . The output of the capture registers  720  is received by the leveling element  725 , which in turn provides an output to the synchronization register  730 . The synchronization register  730  is clocked by a synchronization clock provided by phase-locked loop  750 . The synchronization register  730  provides an output DATAOUT to other circuitry (not shown), for example core circuitry of an FPGA. The delay-locked loop  740  synchronizes to a local clock generated by phase-locked loop  750  and provides a control signal COUNT to delay  710 , such that the DDQS signal is properly phase shifted to clock the incoming data DQ. 
   Without the presence of the leveling element  725 , the data CQ provided by the capture register  720  may be provided to the synchronization register  730  near an active edge of the synchronization clock. Under such a condition, the synchronization register may become unstable and provide incorrect data on the DATAOUT line. Accordingly, the leveling element  725  retimes the output CQ from the capture register  720  as signal LQ, which has a more desirable timing relationship with the synchronization clock. In various embodiments of the present invention, the leveling element  725  may include various circuits. In a specific embodiment of the present invention, the leveling element is a delay line whose delay is varied to avoid meta-stabilities in the synchronization registers  730 . In other embodiments of the present invention, the leveling element  720  includes a register timed by a clock whose phase can be varied. In still other embodiments of the present invention, other circuits, such as a latch, may be used. A timing diagram illustrating the timing of the circuitry of  FIG. 7  is shown in the following figure. 
     FIG. 8  illustrates the timing of the circuitry shown in  FIG. 7 . This figure includes timing for signals DQ  810 , DQS  820 , DDQS  830 , CQ  840 , LQ 850 , synchronization (SYNC) CLOCK  860 , and DATAOUT  870 . The data strobe signal DQS  820  is phase shifted an amount  832  to generate the DDQS signal  830 . The DDQS signal is used to capture the data signal DQ. The output of the capture registers, CQ  840 , follows the clock edges by a clock-to-Q delay  842 . The leveling element  725  phase shifts the data signal CQ  840  an amount  846  to generate LQ  850 , such that the data edge  852  of LQ  850  is away from the rising edges  862  and  864  of the SYNC CLOCK  860 . The DATAOUT signal  870  changes state following a rising edge  864  of the SYNC CLOCK  860  by a clock-to-Q delay  872 . Again, in various embodiments of the present invention, the leveling element may be implemented using various types of circuits. In a specific embodiment of present invention, the leveling element  725  is a delay line. An example is shown in the following figure. 
     FIG. 9  is a block diagram of a portion of a memory interface where a leveling element is implemented as a delay line according to an embodiment of the present invention. This figure includes a capture register, which is implemented as flip-flops FF 1 , FF 2 , and FF 3 , leveling elements, implemented here as delays  940  and  942 , and synchronization register flip-flops FF 4  and FF 5 . Also included are delay  920 , a delay-locked loop  960 , phase-locked loop  970 , and calibration logic  980 . 
   Data DQ is received by capture register flip-flops FF 1  and FF 3  on alternating edges of the DDQS signal. The output of FF 1  is retimed by flip-flop FF 2 , such that the data outputs CQ and CQ 1  are provided by the capture register on rising edges of DDQS. The data strobe signal DQS is delayed to generate the DDQS signal. The outputs of the capture register CQ and CQ 1  are delayed by delay elements  940  and  942  to generate signals LQ and LQ 1 . Signals LQ and LQ 1  are retimed by resynchronization registers FF 4  and FF 5 , which provide data outputs DATAOUT and DATAOUT 1 . The delays provided by delay lines  940  and  942  are adjusted such that instabilities are avoided at resynchronization registers FF 4  and FF 5 . 
   A system clock is received from a crystal oscillator or other period source by phase-locked loop  970 , which in turn generates a local clock and a synchronizing clock. The synchronization clock is tracked by the delay-locked loop  960 , which provides a control signal COUNT to the delays  920 ,  940 ,  942 . This sets the delay through individual delay elements in the delay lines. In this way, as temperature, processing, and voltage vary, the value of the COUNT can be adjusted, thereby keeping the delays at least relatively constant. 
   Accordingly, the COUNT signal is incremented or decremented with changing temperature, voltage, and processing, such that the delays through the delays  940  and  942  remain fairly constant. Again, if data edges of the LQ and LQ 1  signals are near active edges of the synchronizing clock, there may be metastable conditions in the synchronizing registers. Accordingly, the delays of delay elements  940  and  942  are adjusted to avoid these conditions. Specifically, the delays through delay  940  and delay  942  are adjusted by one or more SELECT signals provided by the calibration logic  980 . In this way, the delays provided by the delays  940  and  942  are controlled by the COUNT signal, which adjusts to compensate for temperate and voltage supply changes, and the SELECT signal, which adjusts the delay so data is properly transferred. An example of a delay element that is adjusted in this way is shown the following figure. 
     FIG. 10  illustrates a delay line that may be used as the delay lines  940  and  942  in  FIG. 9 , or as delay lines in other embodiments of the present invention. This figure includes a number of delay elements DE 1 , DE 2 , DE 3 , and DE 4 , the outputs of which are selected by a multiplexer  1020  under the control of one or more select signals provided by a calibration logic circuit. In other embodiments of the present invention, other numbers of delay elements may be used. For example, where finer resolution is needed, more delay elements can used. A delay line having “N” elements will provide a resolution of 360/N. 
   Specifically, a control signal COUNT is provided on line  1004  to the delay elements DE 1 , DE 2 , DE 3 , and DE 4 . This controls the delay through each delay element, such that the delay provided by them has a reduced variability with temperature, processing, and voltage. Specifically, each delay element may be implemented as one or more individual delay circuits, where the delay is dependent on the value of the COUNT signal. For example, each delay element may be one or more circuits having a current discharging a voltage across a capacitor. Alternately, each delay element may include one or more a current starved inverters, where a current starved inverter is implemented as a current source that provides a variable current to an inverter stage. The value of the current can be dependent on the value of the COUNT signal, such that a lower COUNT value provides less current to the inverters, increasing the delay through the inverter. In other embodiments of the present invention, other types of delay elements may be implemented. 
   The signal selected by multiplexer  1020  is provided as a data signal to one of the synchronization registers. The select signal or signals  1006  are generated by a calibration logic circuit, such that metastates or instabilities in the synchronization registers are avoided. An example of how the calibration logic accomplishes this task is shown in the following figure. 
     FIG. 11  is a flowchart illustrating the calibration routine for setting a delay through the delays  940  and  942  in  FIG. 9  or other delays in other embodiments of the present invention. In this method, data is received at a number of possible delay settings. The validity of the data reception at each delay setting is determined, and from this an optimal delay setting is found. 
   Specifically, in act  1110 , an initial delay is set. In act  1120  a test pattern is received. In a typical embodiment of the present invention, this test pattern is received from onboard test registers located on the memory devices, for example, multipurpose registers  404 . 
   In act  1130 , it is determined whether the test pattern has been received correctly. In a typical embodiment of the present invention, data from only one side of each double-data-rate path is checked to determine whether data has been correctly received. For example, in  FIG. 9 , data at the DATAOUT output is checked, while data at the DATAOUT 1  is redundant and is therefore not checked to speed up the calibration routine. In other embodiments of the present invention, only the DATAOUT 1  output is checked, while in others, both outputs are checked. Further, in various embodiments of the present invention, data received by each DQ path in a DQ/DQS group is checked in determining whether data was correctly received, that is, data needs to be correctly received by each DQ path to be considered correctly received. In other embodiments, only one DQ path is checked, again to speed up the calibration routine. In other embodiments, these and other techniques may be mixed. For example, an initial calibration may be performed using each DQ path in a DQ/DQS group, while later adjustments are made using only one DQ path. 
   In act  1140 , the delay is changed. For example, a new multiplexer input may be selected by multiplexer  1020  in  FIG. 10 . In act  1150 , the test pattern is received again, while in act  1160 , it is determined whether the pattern is received correctly. In act  1170 , it is determined whether the last delay has been tested. If not, the delay is changed again in act  1140 . If the last delay has been tested, the minimum and maximum delays where the pattern was received correctly are averaged in act  1180 , and that delay is used as the delay for delay elements  940  and  942 . In an embodiment of the present invention where the delay is incremented or decremented monotonically, the delay is set to the average of the first and last delays where the pattern was received correctly. 
     FIG. 12  is a block diagram of a portion of a memory interface consistent with an embodiment of the present invention. In this embodiment, the leveling element is a register. This figure includes a double-data-rate capture register that is implemented using flip-flops FF 1 , FF 2 , and FF 3 , leveling elements implemented using flip-flops FF 4  and FF 5 , synchronization registers FF 6  and FF 7 , delay element  1220 , delay-locked loop  1260 , and phase-locked loop  1270 . 
   Data is received on the DQ line by flip-flops FF 1  and FF 3  on alternating edges of the delayed DQS signal DDQS. The outputs of the capture register are provided as CQ and CQ 1  on rising edges of the DDQS signal to the leveling elements FF 4  and FF 5 . The leveling elements retime the data and provide outputs LQ and LQ 1  to synchronization registers FF 6  and FF 7 . These registers then provide data outputs DATAOUT and DATAOUT 1  to the core or other circuits. 
   A data strobe signal DQS is received by the delay element  1220 , which phase shifts it to generate the delayed DQS signal, DDQS. A system clock, for example, generated by a crystal oscillator or other source, is received by the phase-locked loop  1270 . The phase-locked loop  1270  generates a local clock for the delay-locked loop  1260 , leveling clocks for the leveling elements FF 4  and FF 5 , and a synchronization clock for the synchronization registers FF 6  and FF 7 . The delay-locked loop  1260  synchronizes to the local clock and generates a digital control signal COUNT, which it provides to the delay element  1220 . 
   In these circuits, data is transferred from capture register flip-flops FF 2  and FF 3  to leveling elements FF 4  and FF 5 , and again from leveling elements FF 4  and FF 5  to synchronization registers FF 6  and FF 7 . Accordingly, the leveling clock should be timed such that metastates and instability are avoided as leveling elements FF 4  and FF 5  receive data from the capture register flip-flops FF 2  and FF 3 , and again as leveling elements FF 4  and FF 5  provide data to the synchronization registers FF 6  and FF 7 . Accordingly, in this embodiment of the present invention, the delay of the leveling clock relative to the synchronization clock is adjusted by the phase-locked loop  1270 , such that data is correctly received and provided to the core circuits. 
   In one embodiment of the present invention, phase-locked loop  1270  provides one leveling clock signal for each DQ/DQS group of signals received by the memory interface. In other embodiments of the present invention, other numbers of leveling clocks may be provided to other groups of signal paths. One method of adjusting a leveling clock timing is shown in the following figure. 
     FIG. 13  is a flowchart illustrating a method of adjusting a phase of a leveling clock according to an embodiment of the present invention. In this method, the phase relationship between a leveling clock signal and a synchronization clock signal is adjusted to optimize data reception by a memory interface. In other embodiments of the present invention, the phase of the leveling clock may be adjusted relative to other clock signals. 
   Specifically, in act  1310 , a phase of a clock generated by a phase-locked loop is set to an initial value. In act  1320 , a test pattern is received. In act  1330 , it is determined whether the pattern was received correctly. In act  1340 , the phase of the clock provided by the phase-locked loop is changed. Again, in act  1350 , a test pattern is received. It is determined whether this pattern was received correctly in act  1360 . In act  1370 , it is determined whether the last phase has been tested. If not, the phase of the clock provided by the phase-locked loop is changed again in act  1340 . If the last phase has been tested, the phase of the leveling clock provided by the phase-locked loop delay is set to the average of the minimum and maximum delays where the pattern was received correctly in act  1380 . In a situation where the delays are incremented or decremented monotonically, the phase-locked loop is set to the average of the first and last delays where the pattern was received correctly. 
     FIG. 14  is a block diagram of a portion of a memory interface circuit according to an embodiment of the present invention. This figure includes a capture register that is implemented using flip-flops FF 1 , FF 2 , FF 3 , leveling registers implemented as flip-flops FF 4  and FF 5 , synchronization registers FF 6  and FF 7 , delay element  1420 , clock multiplexer  1430 , delay element  1440 , calibration logic  1450 , delay-locked loop  1460 , and phase-locked loop  1470 . The data signal DQ is received by capture register flip-flops FF 1  and FF 3 , which are clocked by alternating edges of the DDQS signal. The output of flip-flop FF 1  is retimed by flip-flop FF 2 , such that the capture register provides outputs CQ and CQ 1  on rising edges of the DDQS signal. These output signals are received at rising edges of the leveling clock by leveling element registers FF 4  and FF 5 , which provide outputs LQ and LQ 1  on rising edges of the leveling clock. The synchronization registers FF 6  and FF 7  receive this data on rising edges of the synchronization clock, and in turn provide outputs DATAOUT and DATAOUT 1  to other circuitry, such as core circuits (not shown) on an FPGA. The delay element  1420  delays the DQS signal to generate the delayed the delayed DQS signal DDQS. The phase-locked loop  1470  receives a system clock signal from a crystal oscillator or other periodic signal source, generates a local clock, and provides it to the delay-locked loop  1460 . The delay-locked loop  1460  provides a control signal COUNT to delay elements  1420  and  1440 . The phase-locked loop  1470  also provides the synchronization clock to the synchronization registers FF 6  and FF 7 . 
   The synchronization clock is delayed by delay elements  1440 , which generate a number of clock signals CLK[1:n]. These clock signals are separated in phase from each other, such that the clock multiplexer may select one of a number of clocks having different phases. In a specific embodiment of the present invention, eight clock signals having different phases are provided to the clock multiplexer, one of which is selected and provided as the leveling clock, though in other embodiments of the present invention, other number of clocks may be provided and selected from. These clock signals are multiplexed by the clock multiplexer  1430  to provide the leveling clock signal to the leveling registers FF 4  and FF 5 . The clock multiplexer selection is controlled by calibration logic  1450 . 
   In a specific embodiment of the present invention, a number of clock signals CLK[1:n] are provided to each DQ/DQS group. Each DQ/DQS group includes a clock multiplexer  1430  that selects one of these clocks as the leveling clock for the group. This arrangement limits the number of delay elements  1440  that are needed, but consumes routing resources in delivering clock signals CLK[1:n] to each DQ/DQS group. In other embodiments, the synchronization clock is routed to each DQ/DQS group, each of which has a delay element  1440  and clock multiplexer  1430 . These embodiments reduce the consumed routing resources, but require a larger number of delay elements  1440 . 
   Again, the leveling clock should be timed to avoid metastates and instabilities when the leveling element registers FF 4  and FF 5  receive data from the capture register, and when the synchronization registers FF 6  and FF 7  receive data from the leveling registers FF 4  and FF 5 . Again, at each signal transfer, the provided data should be provided such that register setup and hold times are not violated. Typically this means that the leveling clock should be adjusted such that its edges are away from edges of the data signals CQ and CQ 1 , and that the data signals LQ and LQ 1 , which follow the leveling clock signal by a clock-to-Q delay, should be adjusted such that their edges are away from active edges of the synchronization clock. This adjustment is controlled by selecting one of the clock signals CLK[1:n] using the calibration logic  1450 . An example of how this is done is shown in the following figure. Further safeguards can be implemented to aid in data transfer from register to register as well. For example, delay elements can be selectively inserted. Further, negative-edge triggered registers can be selectively inserted in the signal path, where the negative-edge triggered registers are inserted when needed to provide proper set-up and hold times. Also, since the skews caused by the fly-by topology used for the system clock, additional registers can be selectively inserted or removed such that each group of DQ signals received from the memory devices are transferred from the memory controller to the core circuitry on the same clock cycle. These and other circuit techniques that may be incorporated in embodiments of the present invention are illustrated in co-pending co-owned patent application Ser. No. 11/935,347, filed Nov. 5, 2007, titled “I/O BLOCK FOR HIGH PERFORMANCE MEMORY INTERFACES,” by Bellis et al., which is incorporated by reference. 
     FIG. 15  is a flowchart illustrating the operation of the calibration logic employed by an embodiment of the present invention. In this method, a number of clock signals having different phases are provided to a multiplexer. Test pattern data is received using each of these phases as a leveling clock. At each phase, it is determined whether the data is received correctly, and from this, an optimal phase for the leveling clock is determined. 
   Specifically, in act  1510 , a number of clock signals having different phases are provided as inputs to a clock multiplexer. An initial multiplexer input is selected. In act  1520 , a test pattern is received, for example, from multipurpose registers  404 . In act  1530 , it is determined whether the pattern was received correctly. In act  1540 , a new clock multiplexer input is selected. Again, the test pattern is received in act  1550 , while in act  1560  it is determined whether the pattern was received correctly. In act  1570 , it is determined whether the last clock multiplexer input has been checked. If not, a new clock multiplexer input is selected in act  1540 . 
   If the last multiplexer input has been checked in act  1570 , then the clock phase having a phase equal to the average of the minimum and maximum phases where the test pattern was received correctly is selected as a leveling clock in act  1580 . In various embodiments of the present invention, the clock multiplexer inputs are selected such that the clock phase is monotonically incremented or decremented. In this case, the clock phase having a phase equal to the average of the phases for the first and last clock inputs where test pattern data was received correctly can be used as the leveling clock. 
   Again, in a typical embodiment of the present invention such as the examples shown here, data from only one data path is checked to determine whether data has been correctly received. For example, in  FIG. 14 , data at the DATAOUT output is checked, while data at the DATAOUT 1  is redundant and is therefore not checked to speed up the calibration routine. In other embodiments of the present invention, only the DATAOUT 1  output is checked, while in others, both outputs are checked. Further, in various embodiments of the present invention, data received by each DQ path in a DQ/DQS group is checked in determining whether data was correctly received, that is, data needs to be correctly received by each DQ path to be considered correctly received. In other embodiments, only one DQ path is checked, again to speed up the calibration routine. In other embodiments, these and other techniques may be mixed. For example, an initial calibration may be performed using each DQ path in a DQ/DQS group, while later adjustments are made using only one DQ path. 
   In the above examples, a delay-locked loop generates a control signal COUNT that is used to control the delay provided by various delay elements. For example, in  FIG. 15  a delay-locked loop  1560  generates a COUNT signal that is used by delay element  1420  to generate a phase-shifted DQS signal, and by delay elements  1440  to generate a number of clock signals. An example circuit that may be used is shown in the following figure. 
     FIG. 16  is a block diagram of a delay-locked loop, a delay element, a number of delay elements, and clock multiplexer that may be used to implement the delay-locked loop  1460 , delay  1420 , and delays  1440  in  FIG. 14  or in other embodiments of the present invention. This figure includes a delay-locked loop made up of delay elements DE 1 , DE 2 , DE 3 , and DE 4 , phase detector  1640 , counter  1650 , delay elements DE 5 , DE 6 , and DE 7 , the outputs of which are selected by clock multiplexer  1610  to provide a leveling clock, and delay element DE 8 , which is used to phase shift the data strobe DQS signal to generate a DDQS signal that clocks the input data capture registers. 
   In this example, each of the delay elements DE 1  through DE 8  provide a phase shift that is equal to 90 degrees of the local clock period. In other embodiments of the present invention, other numbers of delay elements can be used, and each delay element may provide a phase shift different than 90 degrees. The local clock is received by delay element DE 1  which phase shifts it and provides it to DE 2 , DE 3 , and DE 4  in succession. The output of this chain is provided to the phase detector  1640 , which also receives the local clock signal. The phase detector  1640  provides a signal that either increments or decrements the COUNT provided by counter  1650 , which provides the control signal COUNT to the delay elements DE 1  through DE 4 . When the delay-locked loop is locked, the local clock and the output of delay element DE 4  are synchronized. At this point, each delay element DE 1  through DE 4  provides a 90 degree phase shift, for 360 phase shift, or one complete cycle in total. The same COUNT signal is used to adjust the delays provided by delay elements DE 5 , DE 6 , and DE 7 . The local clock and the outputs of the delay elements are multiplexed by clock multiplexer  1610  under control of the select signals provided by the calibration logic (not shown). The output of multiplexer  1610  is provided as a leveling clock to leveling registers (not shown). The same COUNT signal is also provided to delay element DE 8 , such that delay element provides a 90 degree phase shift to the DQS signal in order to generate DDQS. 
   This figure includes four delay elements DE 1 , DE 2 , DE 3 , and DE 4  in the delay-locked loop. In other embodiments, other numbers of delay elements may be used. Typically, the delay elements phase shift the clock signal by 360 degrees, or one clock cycle. However, the output of the delay line may be inverted, in which case the delay elements phase shift the clock cycle by 180 degrees, with an additional 180 degrees phase-shift being accomplished by the signal inversion. Where four delay elements are used to delay the clock one cycle, each delay element phase shifts the clock signal 90 degrees. Where “N” delay elements are used, each delay element phase shifts the clock signal by 360/N, or 180/N if a signal inversion is used. Also, for simplicity, only one delay element DE 8  is used to delay the DQS signal. In practical circuits, more delay elements may be used to provide greater flexibility to a user. Further, each delay element may be made up of a number of sub-elements where the number of sub-elements may be varied to provide even further flexibility. For example, one or more such sub-elements may be bypassed using a selection or multiplexer circuit. 
     FIG. 17  illustrates a possible simplification of the circuitry of  FIG. 16  that may be desirable in some embodiments of the present invention. In  FIG. 16 , it can be seen that the function of delay elements DE 1 , DE 2 , and DE 3  are repeated by delay elements DE 5 , DE 6 , and DE 7 . Accordingly, this circuitry may be simplified as shown in  FIG. 17 , in some embodiments of the present invention. For example, in one embodiment of the present invention, delay elements DE 5 , DE 6 , and DE 7  are placed in the memory interface once, and their outputs are routed to a clock multiplexer located in each DQ/DQS group, while the delay elements DE 1 , DE 2 , and DE 3  are also placed once in the memory interface. In this embodiment, it may be desirable to merge the function of the delay elements DE 1 , DE 2 , and DE 3  with the function of delay elements DE 5 , DE 6 , and DE 7 . In other embodiments of the present invention, due to layout proximity or other reasons, such a simplification may be undesirable. For example, in one embodiment of the present invention, delay elements DE 5 , DE 6 , and DE 7  are repeated once and positioned, along with a clock multiplexer, near each DQ/DQS group, while the delay elements DE 1 , DE 2 , and DE 3  are implemented only once for the memory interface. 
   The above description of exemplary embodiments of the invention has been presented for the purposes of illustration and description. It is not intended to be exhaustive or to limit the invention to the precise form described, and many modifications and variations are possible in light of the teaching above. The embodiments were chosen and described in order to best explain the principles of the invention and its practical applications to thereby enable others skilled in the art to best utilize the invention in various embodiments and with various modifications as are suited to the particular use contemplated.

Technology Classification (CPC): 6