Patent Abstract:
The invention relates to an apparatus and method for processing received data (I 1 /Q 1 , I 2 /Q 2 ; d 1 , d 2 ) of a radio interface, wherein the received data includes a sequence of data which have been transmitted for the purpose of error reduction through different branches of a carrier (R k ) of the radio interface, and which are combined into a sequence of data (DATAOUT) to be outputted, wherein the combining is implemented on the basis of carrier information values (R eq,k , SINR k ) of the different branches (k) relative to each other. A maximum ratio combining (MRC) is implemented in which the amplitudes of the branches of the carrier information (R eq,1 , (R eq,2 ) are combined using a division method as a function of a disturbance information value (MIX, SINR 1 , SINR 2 ) of the branches (k).

Full Description:
PRIORITY INFORMATION 
     This application claims priority from German application 10 2004 026 071.0 filed May 25, 2004, which is hereby incorporated by reference. 
     BACKGROUND OF THE INVENTION 
     The invention relates to decoding received data that includes a sequence of data which are transmitted through different branches of a carrier radio interface for the purpose of error reduction, and, undergoing error reduction, which are combined to form a sequence of data to be output, wherein combining is implemented on the basis of carrier information values together with disturbance information values of the different branches relative to each other. 
     While signals or data are being transmitted via a radio interface with multi-path channels subject to fading, highly attenuated carriers (deep fades) are interfered with by superimposed errors. In order to avoid or reduce errors, diversity techniques are employed based on the principle of using independent channels since the low probability that all channels will be subject to simultaneous fading significantly enhances the reception of error-free data or recoverable data. The various diversity techniques serve to provide independent channels by differing means. Diversity significantly improves the required signal-to-noise ratio (SNR) for a specified bit error rate (BER) and allows for a considerably higher time variance while taking into account the maximum Doppler frequency—an important factor for reception by mobile receivers. In addition, diversity may, for example, be employed for synchronization schemes, such as carrier offset estimation, which can be operated with high accuracy, even given a low or negative signal-to-noise ratio. 
     One example of a diversity technique commonly employed is frequency diversity. Here the information or data are transmitted on different carrier frequencies. In order to ensure independent channels, the carrier separation must exceed the coherence width. Another diversity technique is time diversity. This is based on transmitting information distributed over different time slots. This can be achieved, for example, by employing interleaving combined with coding. However, a high level of cost/complexity is required for deep interleaving, with the result that this technique is not suited for applications having a restricted allowable delay. Yet another known commonly employed diversity technique is space diversity or antenna diversity. In space diversity, multiple antennas are employed, either on the transmitter side or the receiver side. In order to ensure independent channels, the antennas must be separated by several wavelengths. 
     The requisite combining of information from two or more receiver branches may vary in terms of the combining site and the combining method. A distinction may be made, for example, between combining before acquisition (i.e., before demodulation) of a received signal, and combining after acquisition (i.e., after demodulation). In Orthogonal Frequency Division Multiplex (OFDM) systems, combining is implemented after acquisition, usually directly after a Fourier transform before the equalizer or after a software-based combining (soft decision), that is, after demapping. 
     In addition, a distinction can be made between selection combining, equal gain combining, and maximum ratio combining. In selection combining, it is simply the branch or path with the highest signal-to-noise ratio that is selected. Implementation is very efficient. However, the information from all the other channels is dropped. 
     In equal gain combining, the signals with all weightings of the branches are set to a unit measure then added. This diversity technique is simpler than maximum ratio combining. However, the technique results in suboptimum efficiency. Maximum Ratio Combining (MRC) employs spatial combining weightings which are selected to maximize the signal-to-noise ratio of the output signal. 
     In order to achieve the maximum signal-to-noise ratio, the diversity branches must be weighted in a maximum ratio combiner by their corresponding fading amplitudes, and the phase shift of the channel must be compensated. The resulting sum must be normalized, thereby yielding the following MRC output value:
 
MRC=( a   1   R   1   e   jΦ1   +a   2   R   2   e   jΦ2 )/( a   1   2   +a   2   2 )
 
where a k  is the amplitude, and Φ k  is the phase of the channel transfer function of the branch k for an instantaneously received carrier R.
 
     These methods are generally known, from European Patent EP 1 125 377, for example, with respect to MRC combining for OFDM systems in a digital television system (e.g., Terrestrial Digital Video Broadcasting-DVB-T). Here, however, a technique is used which utilizes weighting, addition, and division. Interference is not taken into account. Only the channel transfer function and/or soft information is used. U.S. Pat. No. 6,151,372 discloses a method in which weighting, addition, and division processes are employed, an orthogonal detection being used having separate analog-to-digital converters for the I-component and Q-component. 
     However, these diversity methods are disadvantageous. With combining before the Fourier transform, optimization is not possible for each carrier. In software-based combining, use of channel state information (CSI) is not possible during this step. In carrier-based combining, conventional weighting, addition and division methods are employed—with the resulting complexity/expense. In addition, it is not possible to use interference information. To the degree that these methods take into account a noise level, this level is assumed to be constant for all carriers. 
     Therefore, there is a need for an improved technique for processing data which are transmitted through a radio interface by different channels. 
     SUMMARY OF THE INVENTION 
     Accordingly, a method for processing received data, in particular, of a radio interface is advantageous, wherein the received data includes a sequence of data which are transmitted through different branches of a carrier radio interface, for the purpose of error reduction, and, undergoing error reduction, are combined to form a sequence of data to be output, wherein combining is implemented on the basis of carrier information values together with disturbance information values of the different branches relative to each other. 
     A device for processing received data of a radio interface includes a mixer to combine the data of a data sequence, which have been transmitted through different branches of a carrier, based on a disturbance information value and a mixed signal delivery device to provide the disturbance information as a mixed signal, wherein the disturbance information is generated from disturbance information components of the various branches. 
     The disturbance information value is taken into account on a carrier basis. For example, the noise level is not assumed to be constant for all carriers but is instead determined and taken into account for each carrier. 
     Maximum ratio combining may be implemented wherein the amplitudes of the branches of carrier information are combined as a function of the disturbance information values of the branches. 
     Combining may be implemented by mixing the carrier information based on disturbance information values of the different branches weighted relative to each other. 
     The disturbance information may be determined from the signal-to-interference ratios and/or signal-to-noise ratios of the individual branches. In terms of disturbance information values, noise and interference are taken into account either individually or in combination. 
     A disturbance information value may be generated by division of disturbance information components of different branches, for example, according to the equation:
 
MIX=SINR2/(SINR1+SINR2).
 
     A disturbance information value may be generated using approximated division of disturbance information components of different branches, for example, according to the equation:
 
MIX=( X/ 2 x0 )*(2−(( X+Y )/2 x0 ))
 
where X0 is the closest power of 2 and X,Y are the disturbance information components of the different branches.
 
     What is accordingly particularly advantageous is not only the utilization of an exact division but in particular the avoidance of an exact division which would be required for a sequence of weighting, adding, dividing, or would at least be viewed as advantageous according to previously known approaches. A mixer factor can be calculated as the disturbance information, however, using an approximated division of lower precision, without degrading signal quality. 
     The amplitudes of the branches of the carrier information may be determined by a phase correction and a division by an amplitude value for each respective branch, for example, according to the equation:
 
 R   eq,k   =R   k   e   jΦk   /a   k .
 
     The disturbance information of a branch may be determined by a division of the amplitude, or the square of the amplitude, of the branch by the noise components of the branch, for example, by the sum of the noise power level and the interference power level according to the equation:
 
SINR k   =a   k   2 /( N   k   +I   k ).
 
     The branches may be created by different signal transit paths and/or different employed channels of a single sequence of received data. 
     Combining may be implemented after equalizing, where the sequence of data has preferably previously been normalized using the relevant channel transfer function or channel state information. 
     In order to determine a disturbance information value an interference power value may be determined by carrier-based measurements of the average power of a carrier, by employing a time derivative of channel state information of the carrier, and/or by estimating transmitted data. 
     The mixed signal delivery device may include a division device to divide the disturbance information components of the two branches. 
     These and other objects, features and advantages of the present invention will become more apparent in light of the following detailed description of preferred embodiments thereof, as illustrated in the accompanying drawings. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         FIG. 1  is a block diagram illustration of a diversity receiver that receives signals through multiple antennas; 
         FIG. 2  is a block diagram illustration of a second embodiment with an MRC combiner using CSI; 
         FIG. 3  is a block diagram illustration of a third embodiment with an MRC combiner using SINR (signal to interference and noise ratio); and 
         FIG. 4  is a block diagram illustration of a fourth embodiment with combining using a mixer system. 
     
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     The embodiments are based on a design comprising a combiner and employing a mixer system, wherein an approximation is employed for the division. Preferably, optimal efficiency is provided based on carrier-based processing, a combination having the correct maximum ratio, and the use of interference information. 
     What are described here are modified MRC receivers which model crosstalk from intercarrier interference (ICI) as frequency-selective noise, then weight the diversity paths accordingly. Preferably, this MRC modification is usable for all types of frequency-selective noise or frequency-selective interference. For example, long-term measurements of interference on a data carrier can be used for this improved maximum ratio combining (MRC). 
       FIG. 1  illustrates a diversity receiver  100  receiving signals through a plurality of antennas  102 ,  104 , which each provide a received signal to their associated tuner  106 ,  108 , respectively. Each tuner  106 ,  108  provides a signal to an associated one of analog and digital receiver pre-stage,  110 ,  112 , respectively. The analog and digital receiver prestages  110 ,  112  provide processed data to an associated Fourier transformation unit  114 ,  116 , respectively. Each of the Fourier transform units provides frequency domain information to an associated equalizer  118 ,  120 , and an associated circuit to estimate channel, noise, and interference  122 ,  124 . Using a known approach, each of the equalizer circuits  118 ,  120  has two outputs which are applied to a combiner  126 . The combiner  126  implements shared processing of the data applied by the equalizers  118 ,  120 . Data from the combiner  126  are output for further processing to a circuit for demapping and channel decoding  128 . 
     The receiver  100  illustrated in  FIG. 1  is an example of an embodiment having mixing after the Fourier transform wherein a required buffer using the output buffer of the Fourier transform can advantageously be reduced. 
       FIG. 2  illustrates a MRC combiner  200  that includes a synchronization circuit  202  that receives first channel state information value on a line  204  and second channel state information on line  206 . It is, of course, possible to expand this to more than two input branches. The synchronization circuit  202  also receives first and second actual signal or signal ratio I 1 /Q 1 , I 2 /Q 2  on a line  208 ,  210 , respectively. The synchronization circuit  202  outputs two data streams DATA 1 , DATA 2  on lines  212 ,  214 , respectively which are supplied to a combiner  216 . In addition, two channel state information values CSI 1 , CSI 2  on lines  218 ,  220  are supplied to a channel state information processing circuit (CSIP)  222  which processes the channel state information values CSI 1 , CSI 2 . These are processed together. Two signals SINR 1 , SINR 2  on lines  224 ,  226  containing information about the signal-to-noise ratios of the two input signals are output by the CSIP  222 . These two signals SINR 1 , SINR 2  are supplied to a calculation for mixing coefficients (CMC)  228  which outputs a mixed signal MIX on a line  230  and supplies it to the combiner  216 . The channel state information processing circuit (CSIP) also outputs a channel state information value CSIOUT on a line  232  to the combiner  216 . The combiner  216  implements a combined calculation and outputs a sequence of data values DATAOUT on a line  234  and corresponding channel state information value CSIOUT on a line  236 . 
       FIG. 3  illustrates an MRC combiner  300  that receives first and second signal-to-interference-and-noise ratio (SINR) signal on lines  302 ,  204  based on the example of two input branches or signal sequences from two signal sources. Signal sources are understood here to also include data sequences from a single signal source which have passed through different signal paths or signal branches to the receiver, this understanding also applying to the other embodiments. 
     In addition to receiving the signals on the lines  302 ,  304 , synchronization circuit  306  also receives SINR 2 , and first and second actual signals or signal ratios (I 1 /Q 1 , I 2 /Q 2 ) on lines  308 ,  310 , respectively. After appropriate data processing, the synchronization circuit  306  provides corresponding first and second sequences of data DATA 1 , DATA 2  on lines  312 ,  314  to a combiner  326 . The synchronization circuit  306  also outputs two SINR signals or data sequences SINR 1 , SINR 2  on lines  316 ,  318 , respectively to a calculate mixing coefficients circuit (CMC)  320 , the circuit functioning as a mixed signal delivery device. This device  320  provides a mixed signal MIX on a line  322  and a common SINR signal SINROUT on a line  324  to the combiner  326 . The combiner  326  calculates the actual sequence of data DATAOUT provided on a line  328  along with a corresponding SINR and corresponding signal, or a data sequence SINROUT with an associated SINR on a line  330 . 
       FIG. 4  illustrates a mixer system  400  for a combination. Two sequences of data d 1 , d 2  are supplied on lines  402 ,  404 , respectively to a shuffle circuit  406  to which a corresponding selection signal se 1  on a line  408  is also applied. The shuffle circuit  406  should be viewed here as an optional component. Signals or data sequences are output by the shuffle circuit  406  in the low and high states via lines  410 ,  412 , respectively. In a first addition or subtraction device  414 , the data in the high state on the line  412  are subtracted from the corresponding data in the low state on the line  410 . The subtraction result is supplied on the line  416  to a multiplier  418 , which also receives a mixed signal on a line  420 . In the event the shuffle circuit  406  is employed, the values for mixed signal MIX on the line  420  lie between 0 and 0.5. Otherwise the values lie between 0 and 1. Using a second addition circuit  422 , the corresponding data in the high state are added to the thus multiplied or mixed signal, and the resultant sum data DATAOUT is output on line  424 . 
     In terms of the structure of the combiner and its control, the following relationship is utilized. Given the maximum ratio combination, the conventional approach is used to implement a weighting of the input branches, addition and normalization, with the applicable relation being:
 
MRC=( a   1   R   1   e   jΦ1   +a   2   R   2   e   jΦ2 )/( a   1   2   +a   2   2 ).
 
This can be rewritten for the equalized carriers by employing the signal-to-interference-and-noise ratio (SINR) for the individual branches or signal sources to:
 
MRC=(SINR 1   R   eq,1 +SINR 2   R   eq,2 )/(SINR 1 +SINR 2 )= R   eq1 −mix*(R eq1   −R   eq,2 )
 
where
 
 R   eq,k   =R   k   e   jΦk   /a   k  and
 
SINR k   =a   k   2 /( N   k   +I   k ).
 
The subscripts here indicate assignment to the different input branches or signal sources. The variable a k  represents the amplitude, while Φ k  represents the phase of the channel transfer function of the corresponding branch k of the carrier R considered at that instant. In addition, R eq,k  indicates the corresponding value for the carrier after equalization. The shuffle thus results in a simple mixing structure that requires only two additions and one multiplication.
 
     Generation of the signal-to-interference-and-noise ratio (SINR) can be implemented in a variety of ways. In one approach, the ratio can be combined directly by combination to yield a signal-to-interference-and-noise ratio (SINR)=A 2 /(N+I), where A represents the instantaneous amplitude, N the instantaneous noise content, and I the instantaneous interference power. In a second approach, a channel state information value can be determined from the separate values, specifically, from the amplitude A of the channel transfer function, the noise power level N, the measured interference power level I, and the time derivation of the contrast transfer function CTF for the ICI level. 
     The required mixing value MIX for the combination of two branches is then derived to yield:
 
MIX=SINR2/(SINR1+SINR2)= X/Y.  
 
     It should be noted that this division, unlike the conventional approach, is not part of the channel equalization. The precision requirements are thus much lower. 
     To achieve efficient implementation, this division can thus be approximated, for example, by:
 
MIX=( X /2 x0 )*(2−(( X+Y )/2 x0 ))
 
where x0 is the closest power of 2.
 
     In alternative implementation methods, a plurality of variants exists for the described embodiments. For example, implementation without the use of the interference information is possible. In addition, a transfer to the use of more than two receivers or reception branches is possible. This is true in particular for the use of a priority chaining approach. It is also possible to have synchronization between the input branches at different locations within the circuits. Calculation of the mixing value can also be implemented using another division, that is, either with more precision, or only with less precise approximation. 
     Although the present invention has been shown and described with respect to several preferred embodiments thereof, various changes, omissions and additions to the form and detail thereof, may be made therein, without departing from the spirit and scope of the invention.

Technology Classification (CPC): 7