Patent Abstract:
A method of transmitting and rapidly recovering a burst of data without first having to establish a timing or phase lock. The signals are transmitted as modified Manchester coded signals having pulse transitions at a clocking pulse rate which is a multiple of the clocking pulse rate at which the signals are originally generated, and wherein the MOOSE coded signal is modified by ON-OFF keying.

Full Description:
RELATED APPLICATIONS  
       [0001]     This application is a continuation application of U.S. application Ser. No. 09/723,804 filed Nov. 28, 2000. 
     
    
     TECHNICAL FIELD OF THE INVENTION  
       [0002]     The present invention relates generally to methods and apparatus for providing FTTH (Fiber to the Home) bidirectional communications over a single optical fiber, and more specifically to NRZ (Non-Return to Zero) coded signals at a first frequency transmitted downstream and a Manchester coded signal at a second frequency modified by ON-OFF keying and transmitted upstream. The upstream and downstream coded signals are both used to modulate a carrier light wave having a selected wavelength of light, such as, for example, 1310 nanometers of light. The invention further relates to methods and apparatus for transmitting and recovering bursts of data with a minimal number of preamble bits and without first requiring phase lock.  
       BACKGROUND OF THE INVENTION  
       [0003]     The communications industry is using more and more optical or light fibers in lieu of copper wire. Optical fibers have an extremely high bandwidth thereby allowing significantly more information than can be carried by a copper wire transmission line such as twisted pairs or coaxial cable.  
         [0004]     Of course, modem telephone systems require bidirectional communications where each station or user on a communication channel can both transmit and receive. This is true, of course, whether using electrical wiring or optical fibers as the transmission medium. Early telephone communication systems solved this need by simply providing separate copper wires for carrying the communications in each direction, and this approach is still exclusively used in many locations and as part of the transmission path in many others. It is used to a greater degree as the signals get closer to the home or business end users. Although twisted pairs and coaxial cables are more likely to be used in distribution terminals close to the end user and homes, some modem telecommunication systems now use microwave and end-to-end optic fibers as the transmission mediums. In addition, various techniques are often used in optical transmission so that a signal optical fiber can carry more communication in both directions.  
         [0005]     However, because of extremely high bandwidths available for use by an optical fiber, a single fiber is quite capable of carrying a great number of communications in both directions. One technique of optical transmission is WDM (Wavelength Divisional Multiplexing) which uses different wavelengths for different types of transmissions. Typical examples are the use of 1550 nanometers of light for TV signals transmission and 1310 nanometers of light for bidirectional telephony transmission.  
         [0006]     It is noted that the term telephony is used rather than telephone to underscore the fact that communication transmission will include vocal telephone use but is not so limited. Typical telephony systems operate at a single frequency or wavelength of light which is divided into upstream and downstream carefully synchronized time windows for transmitting bursts of data. The use of such upstream and downstream synchronized windows is referred to as TDM (Time Division Multiplexing). This type of telephony systems use a single optical fiber and often may use only a single diode, for both converting electrical signals to optical signals and converting received optical signals to electrical signals.  
         [0007]     However, as mentioned above, optical fibers have extremely high bandwidths and use of an optical fiber as a single bidirectional telephone channel is a very ineffective use of the fiber and, in fact, the available bandwidth of an optical fiber is what makes it possible to use two different and unrelated transmission techniques such as the transmission of bidirectional TDM telephone techniques at one wavelength, and the use of another technique, such as straightforward broadcasting of TV signals downstream at a second wavelength. Typically, two wavelengths regardless of the two techniques being used are combined by the use of WDM technology.  
         [0008]     A major problem for the bidirectional telephony signals is light reflection typically occurring at optical connections or interfaces along the optical fiber, and in a worse case situation, the reflected energy may be interpreted as an actual signal transmission in the bidirectional communication. In addition, the typical use of NRZ (Non-return To Zero) coding and the need for increasing data transmission efficiency by using a minimum number of preamble bits are at odds with each other. Furthermore, clocking pulses and initial pulses of a transmitted signal are typically recovered by establishing a PLL (phase lock loop) by evaluating the time period between high to low and low to high transitions. Thus, since a consecutive string of “1”s or “0”s, using NRZ coding may result in the absence of any transition for an excessive period of time, the effect may be a shift in the timing of a data frame or “wander.” Therefore, a simple and straightforward technique to solve these problems would be of great value.  
         [0009]     Therefore, a technique for transmitting bidirectional telephony signal bursts having minimal energy overlap, occurring from reflection and fast clocking recovery would allow the use of readily available hardware and make efficient and effective use of an optical fiber.  
       SUMMARY OF THE INVENTION  
       [0010]     Shortcomings of the above-discussed bidirectional communication system are overcome by the apparatus and methods of the present invention which comprises generating a first NRZ (Non-Return to Zero) data stream having a first clocking frequency and then transmitting the first NRZ data stream by an optical fiber from a first location to a second location. The data stream is transmitted by modulating a carrier having a selected wavelength of light such as, for example, 1310 nanometers. The selected wavelength of light from the first location is received at the second location and the NRZ data stream is recovered. A second NRZ data stream intended for travel to the first location and also having the first clocking frequency is converted to a Manchester coded data stream at the first clocking frequency. The Manchester coded data stream frequency is then further modified by ON-OFF keying at a second frequency which is a selected multiple of the first clocking frequency, such as, for example, eight times (8×) the first clocking frequency. A particular combination coding discloses as a preferred embodiment herein as MOOSE (Manchester OOK Serial Encoding). The modified combination coded data stream or MOOSE coded data stream generated at the second location is transmitted to the first location by the same optical fiber used by the first NRZ coded data stream and at the same selected wavelength of light. The modified MOOSE coded data stream is then received at the first location where it is converted back to an NRZ data stream having the first clocking frequency without having to first determine clocking signals or establish phase lock loop by reconstructing the Manchester code. The reconstruction is accomplished by delaying the combination coded data stream for a period of time substantially equal to one-half cycle of the second frequency and then combining the delayed signal with an undelayed stream of the combination coded signal.  
     
    
     BRIEF DESCRIPTION OF THE DRAWINGS  
       [0011]     These and other features of the present invention will be more fully disclosed when taken in conjunction with the following Detailed Description of the Preferred Embodiment(s) in which like numerals represent like elements and in which:  
         [0012]      FIG. 1  is a prior art block diagram showing transmission and distribution of a typical coaxial TV and POTS telephone system;  
         [0013]      FIG. 2  shows a prior art POTS telephone system and a fiber optic TV distribution system having 1550 nanometer light carrying TV signals in one direction and 1310 nanometers of light carrying telephony signals in both directions;  
         [0014]      FIG. 3  shows a block diagram of a FTTH (Fiber to the Home) communication system using the present invention and a single optical fiber for carrying the TDM telephony signals in both directions at 1310 nanometers;  
         [0015]      FIG. 4  shows a block diagram of the apparatus and data flow of the present invention;  
         [0016]      FIG. 5A  shows a stream of clocking pulses at about 25 MHZ;  
         [0017]      FIG. 5B  shows an example of an NRZ (non-return to zero) data stream also at approximately 25 MHZ and having a series of data bits 1, 0, 0, 1, 1, 1 and 0;  
         [0018]      FIG. 5C  shows the same series of data bits of  FIG. 5B  using Manchester coding at about 25 MHZ;  
         [0019]      FIG. 5D  shows the same series of data bits of  FIG. 5B  using Manchester coding modified by ON-OFF keying or “MOOSE” coding at approximately 100 MHZ;  
         [0020]      FIG. 5E  shows the same series of data bits of  FIG. 5D  with a selected delay of about 4.8 nanoseconds;  
         [0021]      FIG. 5F  shows the result of combining the signals  FIGS. 5D and 5E  with an OR gate element.  FIG. 5F  is substantially the same as  FIG. 5C ; and  
         [0022]      FIGS. 6A and 6B  show the resulting power spectrum of the downstream and upstream signals, respectively, as a function of frequency.  
         [0023]      FIG. 7A  shows an overlay of the downstream power spectrum and a 14 dB upstream reflection power spectrum as a function of frequency, and  FIG. 7B  shows the resulting isolation of the two power spectrums of  FIG. 7A  as a function of frequency.  
         [0024]      FIG. 8A  shows an overlay of the upstream power spectrum and a 14 dB downstream reflection power spectrum as a function of frequency, and  FIG. 8B  shows the resulting isolation of the two power spectrums of  FIG. 8A  as a function of frequency.  
         [0025]      FIGS. 9A and 9B  show the recovered “eye” pattern of the received 25 MHZ signal and the received 100 MHZ signal, respectively, with no reflection or attenuation.  
         [0026]      FIGS. 10A and 10B  show the recovered “eye” pattern of the received 25 MHZ signal and the received 100 MHZ, respectively, in the presence of 14 dB reflection and 17 dB attenuation.  
     
    
     DETAILED DESCRIPTION OF THE INVENTION  
       [0027]     Referring now to  FIG. 1 , there is shown a typical transmission and distribution system for cable TV and normal telephone service, referred to as POTS (plain old telephone service). As shown, cable TV source location  10  has cable TV transmission equipment  12  which may originate from several sources including a satellite receiver  14 . The TV equipment  12  would then amplify this signal and send it out typically on a coaxial line, such as line  16 , to a distribution system which may include several terminals, such as terminal  18 , where the signal is again amplified and further distributed to an even larger multiplicity of locations. It is possible, of course, that there is no further amplification or distribution, or alternately, such re-amplification and further distribution may occur several times. In any event, the signal will eventually arrive at a local distribution terminal  20  by means of a coaxial cable  12   a  from which it is then distributed to a home or building  22  by a coaxial cable  12   b.  As shown, distribution terminal  20  may also provide TV signals to other buildings or homes, such as indicated by bracket  24 . Once the TV signal is received at building  22 , it will then typically be provided to a TV set  26  directly or to a set-top or cable TV box  28 . If the signal is first provided to the set-top box  28 , it is then directly provided to TV set  26 . It should be appreciated that the direction of travel for such signals may be totally or primarily unidirectional and downstream. That is, it travels primarily from the cable TV signal source  10  to the set-top box  28  in the building or home  22  at frequencies within a frequency band of between 55-870 MHZ, and which TV channels have frequencies of between 55-870 MHZ.  
         [0028]     Also shown is a typical telephone system or POTS which, of course, is two-way communication typically carried by means of a twisted pair of wires. In the example shown in  FIG. 1 , if someone at the cable TV signal source location  10  wishes to talk with someone at building  22 , the telephone  30   a  is used in its normal manner. After substantial switching and routing, the two-way conversation is carried on between the person in building  10  using telephone  30   a  and by a person using telephone  30   b  in the home or building  22 . This communication is typically carried through a twisted pair of wires such as indicated by  32 ,  32   a,  and  32   b.  In recent years, the regular telephone distribution system has also been used to provide communications between computers. This is done by the use of a modem  34  which connects a computer to the telephone line. As was the case with the TV signal distribution, there are typically several stations or substations such as substation  18   a  between the two telephones  30   a  and  30   b  located at the building  10  and the building  22 , respectively. Such distribution terminals or stations allow telephone services between all subscribers with which we are all well aware. However, as shown in portion  20   a  of distribution terminal  20 , there may also be several other buildings or homes connected to telephone distribution terminal  20  as indicated by bracket  24   a.  As was discussed earlier, communications between buildings  10  and  22  were typically accomplished through regular telephone service by individuals talking to each other. However, with more efficient automation, telephone lines may also be connected up to the set-top box  28  as indicated by wires  36 . In addition, in the distribution terminal  38  at the cable TV signal location, there is also a telephone connection  39  to the TV signal equipment  12 , such that it is now possible that a request to purchase movies or information concerning the TV signals and TV equipment can be communicated between the two locations without human intervention.  
         [0029]     As demands increase for more and more TV channels and better and more efficient transmission techniques without disruption and interference, the long runs of coaxial cable are simply becoming inefficient and inadequate. Thus, as is shown in  FIG. 2 , there is an improved system for the transmission of TV signals between the TV signal source location  10  and the building or home  22 . In the systems shown in  FIG. 2 , there is also shown a standard telephone or POTS system as discussed above.  
         [0030]     In the improved television transmission system, however, the transmission is achieved by a fiber optical cable as indicated by fiber optical cables  42  and  42   a.  As shown in  FIG. 2 , the same coaxial cable  12   b  exists between the distribution terminal  20  and the home or building  22 . However, also as shown, distribution terminal  20  includes new equipment  46  which receives the light transmitted on fiber optic  42  and converts it to electrical signals and conversely receives electrical signals from  12   b  and converts the electrical signals to light signals for transmission on fiber optic  42   a.  However, as will be appreciated by those skilled in the art, the TV signals from the TV signal source building  10  normally travel downstream only and are continuous. Thus, it is seen that it is possible by the use of a single fiber optic cable, as well as using existing infrastructure copper wiring such as coaxial cable, to transmit a continuous broad frequency band of TV signals carrying multiple channels of TV information at one wavelength of light. The individual TV channels are then converted to electrical signals at a specific frequency within a selected frequency band, such as, for example, only the 55-870 MHZ frequency band.  
         [0031]     Referring now to  FIG. 3  there is shown a simplified block diagram of the operation of one embodiment of the FTTH (Fiber to the Home) present invention, illustrated as using a single series of optical fibers  42  and  42   a  for the bidirectional telephone transmission between the Optical Interface Unit or OIC  18  located at Central Office  19  and the building or home  22 . It should be noted that, although the following discussion is in terms of a single series of optical fiber cables  42  and  42   a  between the Central Office  19  and Home  22 , there may also be one or more amplification stations located at various locations in the distribution path.  
         [0032]     Further, as is shown, in addition to the series of optical fibers  42  and  42   a  traveling between OIU (Optical Interface Unit)  18  at Central Office  19  and a distribution terminal  20 , hereinafter referred to as the HNU (Home Network Unit), there will be other optical fibers as indicated by optical fibers  42   b  through  42   d  which extend between one-to-four Optical Splitter/Coupler  44  and other home distribution terminals or HNU&#39;s similar to HNU  20 . Each of the optical fibers  42   b  through  42   d  may carry light at both 1550 nanometers and 1310 nanometers.  
         [0033]     As shown, TV signal source location  10  provides signals from equipment  12  and, in this illustrated embodiment, the TV signals may be 55-870 MHZ signals provided to a coupler or WDM (Wave Division Multiplexer)  50 . It will be appreciated that cable  16  could be either an optical fiber or a coaxial cable. A copper coaxial cable  16  would carry the TV signals having a bandwidth of 55-870 MHZ to circuitry  51  which uses the electrical TV signals to modulate light having a selected wavelength which is directed or focused onto optical fiber  52 . In one preferred embodiment, a particular selected wavelength for such TV signals is 1550 nanometers. Thus, the 1550 nanometer light waves are provided to optical fiber  42  by WDM  50 , and according to one embodiment, travel in a single direction from WDM  50  through optical fibers  42  and  42   a  to distribution terminal or HNU  20  in house or building  22 . Of course, once the 1550 nanometer light carrying the TV signal arrives at HNU  20 , photo-diode or PD  57  strips out the TV signals such that they can be distributed throughout home or building  22 , as shown by coaxial cable  12   b  carrying the signals to set up top box  28  and/or television  26 .  
         [0034]     Also as shown, electrical telephony or POTS (Plain Ole Telephone) signals may be carried to Central Office  19  by copper wires, such as copper wires  48 , which represent a twisted pair of normal telephone communication wires. Circuitry or OIU  18  in Central Office  19  receives these electrical telephony signals as well as other broadband data signals traveling downstream. As will be discussed in detail later with respect to  FIG. 4 , Circuitry  18  generates a coded form of these data signals to modulate light at a selected wavelength (typically by a laser diode—(LD)  53 ). In the same manner, light at that same wavelength traveling upstream and also previously modulated by electrical telephony signals is detected (typically by a photo detector—(PD)  55 ) and processed to recover the telephony signals. Thus, the fiber optic cables  42  and  42   a  shown between OIU  18  and home or destination  22  carries telephony signals at a single wavelength of light typically selected to be about 1310 nanometers, fibers  42   a  through  42   d,  there will be a plurality of additional optical fibers  54   a  through  54   c  also carrying many other telephony signals at 1310 nanometers.  
         [0035]     Thus, ONU  18  which is connected to fiber optic cable  42  (through SWX  50 ) for carrying the 1310 modulated light may also receive 55-870 MHZ TV signals from the TV signal source location  10 . The 55-870 MHZ electrical signals may, as an example, be used to modulate light having a wavelength of 1550 nanometers. SWX (Splitter with Division Multiplexing)  54  then combines by WDM (Wave Division Multiplexing) the plurality of 1310 nanometer wavelength signals along with the 1550 nanometer wavelength signals such that cables  42  and  42   a  carrying the TV signals in a downstream direction on 1550 nanometer light and carries bidirectional telephony signals in both directions at 1310 nanometers of light. Of course, fiber optical cables  42   b  through  42   d  and connected to coupler/splitter  44  carry the 1550 nanometer light and the 1310 nanometer light in a similar manner.  
         [0036]     At the downstream destination, the bidirectional telephony signals traveling on 1310 nanometer light waves are routed to equipment in HNU  20  in Home  22  which recovers the electrical telephony signals by a photo detector—(PD)  56  from the 1310 nanometer light waves traveling downstream and uses the electrical telephony signals traveling upstream to modulate light waves having a wavelength of 1310 nanometers by laser diode—(LD)  58 . The electrical telephony signals are then distributed from HNU box  20  by wire pair  32   b  to the telephone  30   b  or other telephony equipment such as the 56K telephone modem  34  at home or building  22 .  
         [0037]     As was discussed above, the extremely broad bandwidth available with the use of optical fibers as a transmission medium offers many advantages and vastly increases subscriber density on a single fiber. Unfortunately, new uses and demands continue to grow at ever-increasing rates. Consequently, what may have appeared to be an overabundance of bandwidth for years to come a couple of years ago is already or threatens to become crowded in the near future. In addition, every technology has its own special set of problems and the use of optical fiber as a transmission medium for telephony communication is no exception. More particularly, using present techniques, a light wave traveling through a fiber is particularly vulnerable to reflection if the connector joining the two fibers is dirty or improperly fitted. The present invention, however, discloses transmission techniques, coding, or protocols to minimize the effects of reflective overlap of the transmitted energy spectrum, and rapid clocking recovery.  
         [0038]     Referring now to  FIG. 4 , there is shown a block diagram illustrating the features of the present invention. It should be noted that elements of  FIG. 4 , which are common with the elements of  FIG. 3 , may carry the same reference numbers. To aid in understanding the invention, the following embodiment of the invention is described assuming a two-way communication exchange extending at least between OIU  18  at a first location or Central Office  19  and a second location or HNU  20  in Home  22 .  
         [0039]     According to the described embodiment, a first data stream of electrical pulses in NRZ (Non-Return to Zero) format and clocking signal having a selected frequency are received through the back plane by FPGA (Field Programmable Gate Array)  60  for conditioning at inputs  62  and  64 , respectively. Control and synchronizing information along with addresses and alarm data is added to the data stream by FPGA  60 . The stream of conditioned NRZ coded signals are then transmitted by line  65  to a low pass filter  66  located in OIU  18  at Central Office  19 . In a preferred embodiment, the NRZ electrical pulses have a frequency of around 25 MHZ. More specifically, using standard and readily-available components and parts, this frequency will actually be about 25.92 MHZ. Low pass filter  66  will typically be chosen so as to readily pass frequencies less than about 25 MHZ, while substantially blocking all frequencies above about 30 MHZ. Referring briefly to  FIG. 6A , and, as will be discussed in more detail later, line  68  represents the attenuation vs. frequency of low pass filter  66 . As shown, LPF  66  substantially allows all frequencies to the left of line  68  to pass, while substantially attenuating everything to the right of line  68 . The 25 MHZ NRZ data stream is then provided to laser driver  70  which adjusts or regulates the signal to provide for diode bias, power output of the diode and modulation level. The properly adjusted and regulated signal is then provided to laser diode (LD)  53  in duplexer  73  for modulating light waves having a nominal wavelength of about 1310 nanometers. This modulated light at 1310 nanometers is injected or focused directly onto optical fiber  42 , or alternatively, as shown in dashed lines, the modulated light may first be provided to a WDM (Wave Division Multiplexer)  50  which combines the modulated 1310 nanometer light with another light frequency (such as 1550 nanometer) from optical fiber  52 .  
         [0040]     The 1310 nanometer light carrying the NRZ data stream on fiber  42  is then provided through a splitter such as 1×4 splitter  44  to optical cable  42   a  and then to the distribution panel  20  in home or building  22 . Splitter  44  also provides individual fiber optical cables  42   b,    42   c  and  42   d  to other homes or buildings which also receive the data stream. Cable  42   a  is then provided to a Quplexer  82  located in distribution panel  20 , which separates out the 1550 nanometer light carrying the TV signals, if any, as shown at  84 , and passes the 1310 nanometer light modulated by the NRZ coded data stream to photo diode  56 . Photo diode  56  in Quplexer  82  along with the very low noise amplifier recovery circuit  86  recovers the 25 MHZ NRZ coded data stream adds gain and converts this data stream to a differential voltage output on a pair of electrical conductors  88   a  and  88   b.  The two different voltage outputs are provided to low pass filter  90  and then onto Comparator or Quantizer  92 . Comparator  92  uses the two signals on line  88   a  and  88   b  to regenerate the 25 MHZ NRZ data stream by improving the signal and increasing the signal-to-noise ratio such that the output of Comparator or Quantizer  92  is suitable for use by TLL Logic. This output of Quantizer  92  is then provided to PLL (Phase Lock Loop Circuit)  94  to recover the 25.92 NRZ data as well as the 25.92 clocking pulses. The 25 MHZ NRZ data is then provided by line  96  to receiving equipment.  
         [0041]     The transmission path from the HNU  20  in the second location or Home  22  to OIU  18  at the Central Office  19  in earlier optical transmission systems might well have been a mirror image of the transmission sequence from OIU  18  to HNU  20  as discussed above. However, to assure efficiency and transmission integrity, the present invention uses a first NRZ coded transmission protocol to carry information in one direction at a first frequency of 25.92 MHZ as just discussed, and a modified Manchester coded transmission protocol at a second frequency to carry information in the opposite direction. The modified MOOSE coded data is referred to herein as Manchester/OOK coded data and provides transitions which are eight times (8×) the first frequency.  
         [0042]     Referring now to  FIGS. 5A through 5F , there is shown a first clocking signal of approximately 25 MHZ (actually 25.92 MHZ) at  FIG. 5A  and an NRZ digital data stream at  FIG. 58  having bits  98  through  110  which represent binary bits 1, 0, 0, 1, 1, 1 and 0, respectively.  FIG. 5C  shows a typical Manchester coded data stream representing the same data stream of “1”s and “0”s as shown in the NRZ code of  FIG. 5B . That is,  FIG. 5B  shows the NRZ code and  FIG. 5C  shows the Manchester code for the data sequence 1, 0, 0, 1, 1, 1, 0. As is recognized by those skilled in the art, one advantage of Manchester code over NRZ coding is that there are twice as many signal transitions or leading and trailing edges as present in an NRZ stream of data. In fact, when an NRZ data stream has a string of consecutive “1”s or “zeros,” there are no transitions at all during such a consecutive stream.  
         [0043]     Referring again to  FIG. 4  and  FIG. 5 , the modified Manchester code protocol for data transmission from HNU  20  to in Home  22  to OIU  18  at Central Office  19  according to this invention will be discussed. As shown, in  FIG. 4  and  FIGS. 5B and 5C , an NRZ data stream ( FIG. 5B ) is provided along an electrical conductor  112  to circuitry  114  which converts the NRZ coded data stream on line  112  to an equivalent standard Manchester coded data stream on line  116  ( FIG. 5C ), also at 25.92 MHz. As discussed above, there are no signal transitions during the stream of connector “1”s represented by bits  104 ,  106  and  108  for the NRZ data stream of  FIG. 5B . However, each of the Manchester coded data bits  104 ,  106  and  108  shown in  FIG. 5C  have two transitions. It will be appreciated that coding circuitry  114  could simply convert the 25 MHz NRZ data stream to a 25 MHz Manchester coded data stream as shown in  FIGS. 5A and 58  and then transmit this 25.92 MHz Manchester coded signal to OIU  18  for information traveling from HNU  20  to OIU  18  with improved performance. It is noted that converting a 25.92 MHz NRZ coded signal to a 25.92 MHz Manchester coded signal requires a clocking signal which is twice the original 25.92 MHz clock. However, even significantly greater improved performance can be achieved by first converting the data stream traveling from HNU  20  to OIU  18  to a modified Manchester coded data stream which includes transitions at a frequency which is a multiple of the frequency of a 25.92 MHz Manchester coded data stream.  
         [0044]     Referring again to  FIG. 5C , there is shown the Manchester coded data stream which is the equivalent of the original 25 MHz NRZ data stream of  FIG. 5D .  FIG. 5D  is a combination Manchester code passed through an ON-OFF Keying code device  118  and will be referred to herein as MOOSE coded signal according to the teachings of this invention. The ON-OFF coding device  118  receives the Manchester code and simply provides a reference voltage level such as a zero or “off” output for those portions of the Manchester coded bit that are already at zero and a repetitive switching between on-off, “one”-“zero,” or “first level”-“second level” output for those portions of the Manchester coded bit that are “on” or equal to “1.” For example, the first half  120  of bit  100  of  FIG. 5C , is zero volts, so according to one embodiment, the first half  122  of bit  100  of the Manchester/OOK coded signal shown in  FIG. 5D  is also zero. However, the second half  124  of bit  100  of  FIG. 5C  is a “1,” and therefore the repetitive ON-OFF keying by device  118  results in the second half  128  of bit  100  which is shown in  FIG. 5D  as a series of on-off pulses. It should be understood that the reference voltage could be selected by a “1” rather than a “zero” such that the high or “one” portion of the bit results in a continuous “1” and the “zero,” or low portion of the bit could be switched between the reference “high” voltage and a second voltage which is, for example, “zero.” Likewise, it is possible to set the reference voltage for a voltage level different than the voltage level of the portion of the bit it represents. The rate of the on-off cycle depends on the clocking signal as determined by clock multiplier  130  on line  132  to ON-OFF keying device  118 . In the embodiment shown, clock multiplier  130  increases the 25.92 MHZ input clocking rate eight times (8×) to 207.36 MHz. Consequently, the ON-OFF portions of the Manchester/OOK coded data of  FIG. 5D  has a frequency four times (4×) that of the NRZ data of  FIG. 5B . More specifically, for every NRZ coded bit ( 98  through  110 ) shown in  FIG. 5B , there is a Manchester coded bit in  FIG. 5C  with at least two voltage level transitions. However, there are a minimum of four transitions as shown in  FIG. 5D  for the 103.68 MHz Manchester/OOK coded signals. The increased number of leading edge and trailing edge transitions of the data stream of  FIG. 5D  helps to assure data integrity, and, as will be discussed later, provides greater isolation or separation of the signal power spectrum and allows a fast clock recovery without first having to obtain a data lock by a phase lock loop.  
         [0045]     The unique Manchester ON-OFF Keying or MOOSE coded data signal is then provided from ON-OFF keying device  118  to BPF  134 , TX driver circuit  136  and then to diode  58  in Quplexer  82  where it is used to modulate light directed onto optical fiber  80  for transmission to distribution terminal  18 . Referring to  FIG. 6B  line  140  between about 50 and 60 MHz and line  142  between about 150 and 160 MHz shows the pass-no pass threshold of Band Pass filter  134 . That is, only the signals which occur between line  140  and  142  can pass through the filter  134  to diode  58  to modulate the 1310 nanometer light. The 1310 nanometer light modulated by the MOOSE coded data stream is then provided to photo diode PD  55  and TIA or Transimpedance Amplifier  146  such that the MOOSE coded electrical signal data is recovered as a pair of voltage differential signals on lines  148  and  150 . A transimpedance amplifier is a low noise amplifier which converts current to voltage. Low Pass Filter  152  operates on the MOOSE coded signal in the same manner as discussed above with respect to the NRZ signal traveling from OIU  18  to HNU  20 . However, unlike the processing of the NRZ data stream discussed above, the two outputs of low pass filter  152  are provided to a Limiting Amplifier  154 . Limiting amplifier  154  amplifies each of the signal excursions as necessary to obtain an output signal where all of the “peak” values are at a predetermined level even if the “peak” values provided by Low Pass Filter  152  varied significantly. The two differential voltage outputs of Limiting Amplifier  154  are then provided to another Band Pass Filter  156  to again remove any noise or signals outside of the 50 MHZ to 160 MHz frequency band.  
         [0046]     The output  158  is split and applied to delay line  160  and multiplier  162 . Similarly, the reference output  164  is split and applied to delay line  166  and multiplier  168 . According to the present embodiment, delay lines  160  and  166  provide a delay of approximately 4.8 nanoseconds as shown in  FIG. 6E .  
         [0047]     Referring now to  FIG. 6D , there is shown an idealized version of the recovered MOOSE code on line  158  prior to being applied to combining circuit  162 .  FIG. 6E  shows an idealized version of the MOOSE code after being delayed for 4.8 nanoseconds as would be present on line  146  and prior to being applied to combining circuit  168 .  FIG. 5F  shows the output of combining circuit  168  after combining the data streams of  FIGS. 5D and 5E . It will be appreciated that  FIG. 5F  is the same as the Manchester coded data stream of  FIG. 5C , and thus the original upstream signal has been recovered without first establishing the timing clock signals or a phase lock. After further conditioning by Comparator  170  and Low Pass Filter  172 , the Manchester coded data stream at 25.92 MHz will again be suitable for use by TTL circuitry. The 25.92 MHZ Manchester coded output of Low Pass Filter  172  is then provided to Manchester decoder  174  to recover the transmitted clock and to convert the Manchester coded data stream back to an NRZ data stream which is the original form of the data. The clocking signal and the recovered NRZ data stream are then provided to FPGA  60  for further routing of the signals through the back plane.  
         [0048]     Referring now to  FIGS. 6A and 6B , there is shown the power spectrum of the downstream and the upstream signal transmissions, respectively, according to the teachings of the invention. Referring to  FIG. 6A , there is also shown the threshold line  68  of the low pass filter circuitry  90  shown in  FIG. 4 . As can be seen, the low pass filter  90  is chosen to readily pass all frequencies less than about 20 MHZ and to substantially attenuate frequencies (for example, 40-50 db of attenuation) above about 30 MHZ. Thus, as shown in  FIG. 6A , the single burst  176  of NRZ data to the left of line  68  and which is about 25 MHz and less along with harmonics and other noise is transmitted and received at the downstream distribution terminal  20 . However, after being passed through LPF  90 , all of the higher frequency signals to the right of line  68  are heavily attenuated and will not be passed to Comparator  92 .  
         [0049]     In a similar manner, the data transmitted and received upstream at terminal  18  is passed through a band pass filter  156  which readily passes frequencies of between about 50 MHz and 150 MHz while substantially attenuating frequencies having a frequency of less than about 50 MHz and greater than about 150 MHz. The threshold (pass-no pass) lines  140  and  142  thus clearly illustrate how the upstream transmitted data is limited to the center burst of data  178  between 50 MHz and 150 MHz.  
         [0050]      FIG. 7A  shows the overlay of the signal  176  transmitted downstream and received at terminal  20  after it has passed the low pass filter  90 . Curve  180  shows the power spectrum of a “reflected” signal (intended for transmission from terminal  20  to terminal  18 ) due to a bad optical connection or other anomaly in the optical line. Since all of the downstream data is carried by a burst of data of about 25 MHz and since the frequency above about 25 MHz are substantially attenuate, the only portion of the reflected transmission that can cause cross-talk or noise is that portion of curve  180  to the left of line  182  which is less than 25 MHz.  
         [0051]     Referring now to  FIG. 7B , the portions of the power spectrum of  FIG. 7A  between 0 and 25 MHz is expanded and line  184  illustrates that the isolation between the actual signal and the reflected signal is between 75 dB and a worse case of 50 dB which is still excellent.  
         [0052]     Similarly,  FIG. 8A  shows an overlay of the signal  178  transmitted upstream and received at terminal  18  after it has passed through band pass filter  156 . Curve  186  shows the power spectrum of a reflected signal originally intended for transmission downstream from terminal  18  to terminal  20 . Since all of the data is carried by a power burst at frequencies between about 50 MHz and about 150 MHz and, since all of the frequencies outside of this band are substantially attenuated, the only portion of the reflected transmission that can cause noise and/or create cross-talk are those portions of curve  186  which is between 50 and 150 MHz. Therefore, the curve or line  188  of  FIG. 8B  expands the frequency band between about 50 MHz and 150 MHz and illustrates the isolation between the transmitted signal  178  and the reflected signal  186 . As shown, the isolation is still very substantial. As shown, it varies from a worse case of about 35 dB up to about 75 dB.  
         [0053]     Referring now to  FIGS. 9A and 9B , there is shown the “eye” pattern for the recovered upstream and downstream signals with a good, clean signal and no reflection. It will be appreciated by those skilled in the art, what is meant by the “eye” pattern is the volume level separation between the digital high and low or “1”s and “0”s signals. As shown, there is a substantial separation of the received 25 MHz downstream signal and the received 100 MHz upstream signal.  
         [0054]      FIGS. 10A and 10B  show the eye patterns for the same upstream and downstream signals when they are also subjected to a 14 dB reflected signal and a 17 dB attenuation. As shown, the “eye” patterns are still very distinct, although the amplitude separation of the 25 MHz received signal is reduced as is the amplitude separation for the 100 MHz.  
         [0055]     The corresponding structures, materials, acts, and equivalents of all means or step plus function elements in the claims below are intended to include any structure, material, or act for performing the function in combination with other claimed elements as specifically claimed.

Technology Classification (CPC): 7