Patent Abstract:
Circuitry and methodology for transferring a representation of a data signal between clock domains. In particular, the disclosure teaches a method for creating representations of signals input from a slow clock domain into a fast clock domain and vice versa. The methods and apparatus use a RAM-free architecture which may be easily incorporated into integrated circuits to enhance efficiency.

Full Description:
CROSS-REFERENCE TO RELATED APPLICATIONS 
     The present application claims the priority of Provisional Application Serial No. 60/232,554, filed Sep. 14, 2000, in accordance with 35 USC §120. 
    
    
     FIELD OF THE INVENTION 
     The present invention relates to improved electronic circuits for the transmission of data between different clock domains. More particularly, the present invention relates to electronic circuits useful for the conformational representation of signals communicated between parts of circuits having different frequency clocks. 
     BACKGROUND OF THE INVENTION 
     Many electronic circuits and domains within circuits operate at rates which are determined by clock cycles generated at a particular domain clock frequency and transmitted to them. The term clock domain is used hereinunder to mean those parts of an electronic circuit that operate at the rate of a particular clock. These clock frequencies often vary among said clocks domains, varying accordingly the operating frequencies of the circuits in their domains. It is often necessary to generate a digital representation of the duration of a signal, expressed in terms of the number of clock cycles of its domain of origin, represented by signals of that domain frequency, and to transmit this digital representation to a destination clock domain, while converting the digital representation, generated by the origin domain clock, to that of the destination domain clock frequency. 
     In the past, when a signal needed to be transmitted from a fast clock domain to a slow clock domain, the signal would first need to be written by a processor from the fast clock domain to random access memory across a bus. Then a processor in the slow clock domain could read the signal across the bus from the random access memory at its own slow clock speed. However, this architecture and process requires a large number of read/write operations which directly affects the overall efficiency and performance of a system so designed. 
     SUMMARY OF THE INVENTION 
     The conversion of the transmitted digital representation of the number of clock cycles forming a signal from one clock domain frequency into another clock domain frequency, while retaining the number of cycles, is called hereinunder “conformation”. 
     As alluded to above, conformation poses problems, and particularly in the two following cases: 
     transmission of signal representation by slow clock signals (hereinbelow LF), i.e. long clock cycles, to a fast clock signal, short clock cycle domain (hereinbelow HF). In this case, some or all of the LF clock cycles may be sampled more than once by an HF domain device, leading to erroneous interpretation of the signal by the HF domain; and 
     transmission of signal duration representation by HF clock cycles to an LF domain. In this case, sampling of HF clock cycles by an LF clocked device may lead to erroneous interpretation of the signal as some of the short HF cycles will not be sampled by the LF device at all or an HF signal that is not a full integer multiple of LF cycles in length will be assigned an incorrect length by the LF device. 
     It is the purpose of the present invention to offer efficient circuits that overcome the aforementioned problems. 
     This is accomplished by the following two kinds of methods: 
     [1] For transmitting a data signal from a fast clock domain directly to a slow clock domain, a circuit, which bridges the two domains, detects the presence or absence of signal at every clock cycle in the fast domain, presence or absence being assigned a value, e.g. high vs. low (or 1 vs. 0) for each clock cycle. A plurality of the clock signal detection values is transmitted in parallel to a counter in the slow clock domain wherein each clock signal detection value is recorded as being a high or a low, and wherein the total number of detected high values or detected low values is output as a binary number by counter, thus informing the slow clock domain of the true number of clock cycles of which the signal is comprised; and 
     [2] For transmitting a data signal from a slow clock domain directly to a fast clock domain, a circuit which bridges the two domains comprises, in the slow clock domain, an edge detector for detecting the rising edge or falling edge of an incoming signal. When the edge detector detects a signal&#39;s leading edge, it causes the reversal of the state of flip-flops in both the slow domain and the fast domain, thereby signifying advent of a signal. Reversal of the flip-flops in the slow domain for each clock cycle when a signal is passing, is detected in the fast domain and understood by the fast domain as being caused by a new slow clock cycle, thereby sensitizing the fast clock domain to the beginning and ending of slow clock cycles which it would otherwise lump together as being a single clock cycle. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is a block diagram of a conformational timer circuit for the conformational representation of signals generated in a slow-clock domain and transmitted to a fast-clock domain; 
     FIG. 2 is a timing signal relationship diagram of the conformational timing circuit shown in FIG. 1; 
     FIG. 3 a  is a block diagram of the fast-clock domain signal generating portion of a conformational timer circuit in accordance with an exemplary embodiment of the present invention; 
     FIG. 3 b  is a block diagram of the slow-clock domain portion of a conformational timer circuit for processing signals generated in and transmitted from the fast clock domain shown in FIG. 3 a , hereinabove, in accordance with an exemplary embodiment of the present invention; 
     FIG. 4 a  is a block diagram of the fast-clock domain signal generating portion of a conformational timer circuit in accordance with an exemplary embodiment of the present invention; 
     FIG. 4 b  is a block diagram of the slow-clock domain portion of a conformational timer circuit for processing signals generated in and transmitted from the fast clock domain shown in FIG. 4 a , hereinabove, in accordance with an exemplary embodiment of the present invention, wherein the frequency ratio between the domains is less than 2; and 
     FIG. 5 is a signal relationship wave diagram of the conformational timer shown in FIGS. 4 a  and  4   b , in accordance with an exemplary embodiment of the present invention. 
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     Referring now to FIG. 1, block diagram  100  depicts an exemplary embodiment of a circuit for conformational representation of signal  112 . Signal  112  originates in a slow-clock domain  110 , which includes Slow Signal Splitter  120  (hereinbelow “SSS”) for the processing of signal  112 , whose processed output is transmitted into HF domain  150 . HF domain  150  includes conformational timer  160  (hereinbelow “SYN”). Components of slow-clock domain  110  are clocked by LF cycles from LF clock (not shown), applied by lead  111 . Components of slow-clock domain  150  are clocked by HF cycles of HF clock (not shown) applied by lead  151 . Incoming signal  112 , to be conformationally timed, is applied to a SSS  120 . SSS  120  comprises a double-input modulo- 2  adder XOR gate  122 , an feedback flip-flop  124 , an inverter  126 , and two double-input AND gates  128  and  130 . 
     Incoming signal  112 , having a duration of several LF line  111  clock cycles, is an input into AND gates  128  and  130  and into XOR gate  122 . XOR gate  122  output is applied to the D input terminal of feedback flip-flop  124 . The flip-flops of this embodiment are assumed to be of rising edge logic, although other logic could also be used. The first output of port Q of feedback flip-flop  124  is delayed by one LF clock period relative to signal  112 , and is: 
     applied as a second input into AND gate  128 ; 
     applied as a second input into AND gate  130  after its inversion by inverter  126 ; and is 
     fed back to constitute the second input into XOR gate  122 . As long as signal  112  is “1” (logical high), one of the outputs of gates  128  and  130  must be “1” (logical high) and the other must be “0” (logical low), generating complementary outputs of logical high and of logical low, respectively. The output of gate  128 , applied to lead  132 , is named inc_odd_slow, and the output of gate  130 , applied to lead  134 , is named inc_even_slow. These outputs alternate at one half of the LF clock frequency as long as signal  112  is logical high. 
     Referring now to fast clock domain  150  which includes: 
     HF clock output lead  151 , and 
     conformational timer  160 . 
     Conformational timer  160  comprises of: 
     Odd branch  161 , its input lead  132  and its output lead  168 , 
     Even branch  181 , its input lead  134  and its output lead  188 , 
     XOR gate  170 , its input leads  168  and  188 , and its output lead  192 . 
     XOR gate  170  output, applied to lead  192 , is the conformationally timed signal that constitutes this inventive circuit output. 
     Referring now to the operation of odd branch  161 , lead  132  output inc_odd_slow is applied to the D terminal of flip-flop  152 , whose Q terminal output is applied to the D terminal of flip-flop  154 . Two serially connected flip-flops  152  and  154  are needed due to signal stability reasons, as is known. The Q terminal output of flipflop  154  is applied both to the D terminal of flip-flop  156  and to one input terminal of a two terminal AND gate  166 . The Q terminal output of flip-flop  156  is inverted by inverter  160 , and the output of inverter  160  is applied to the other input terminal of gate  166  via lead  162 . The output of terminal Q of flip-flop  154  is delayed by two rising edges of HF clock signals behind output  132 , and the output of terminal Q of flip-flop  156  is delayed by three rising edges of HF clock signals behind output  132 , i.e. one HF rising edge behind flip-flop  154 . The output of AND gate  166  is high only when the output of flip-flop  154  is high and the output of gate  156  is low, i.e. if the output cycle at the two rising edges of HF period delay is high while the output cycle at the three rising edges of delay is low. This occurs when the output of line  132  changed from low to high between these two rising edges. 
     The operation of even branch  181  is similar to the operation of odd branch  161 . Lead  134  output inc_even_slow is applied to the D terminal of flip-flop  172 , whose Q terminal output is applied to the D terminal of flip-flop  174 . Two serially connected flip-flops  172  and  174  are needed due to signal stability reasons, as is known. The Q terminal output of flip-flop  174  is applied to the D terminal of flip-flop  176  and to one input terminal of a two terminal AND gate  186 . The Q terminal output of flip-flop  176  is inverted by inverter  180  and the output of inverter  180  is applied via lead  182  to the other input terminal of gate  186 . The output of terminal Q of flip-flop  184  is delayed by two rising edges of HF clock signals behind the output of  134  and the output of terminal Q of flip-flop  176  is delayed by three rising edges of HF clock signals behind the output of  134 , i.e. one HF period behind flip-flop  174 . Only if the output of flip-flop  174  is high while the output of gate  176  is low, the output of AND gate  186  is high, i.e. the output cycle at the two HF period delay is high while the output cycle at the three cycle delay is low. This occurs when the output of line  134  changed from low to high between these two cycles. 
     Referring now to FIG. 2 of the timing diagrams of various electrical signals shown in FIG. 1, line  1  shows the logical levels of the LF clock cycles, of 77.76 Mhz in this embodiment, and line  2  shows the logical levels of the HF clock cycles, of 100 Mhz in this embodiment. Full vertical lines mark the start of each LF cycle, while dotted vertical lines mark the start of each HF cycle. Line  3  shows the logical levels of the inc_odd_slow signal, lead  132 , represented by cycles of one half of the LF frequency and line  7  shows the logical levels of inc__even_slow signal, lead  134 . Line  4  shows the output of odd_clkd 1  of Q terminal of flip-flop  152  into lead  153 , rising to logical high after a logical high of  134  and after rising HF clock signal. Line  5  shows the output of odd_clkd 2  of Q terminal of flip-flop  154  to lead  155 , delayed by one HF clock signal relative to odd_clkd 1 , and line  6  depicts the odd branch output odd_cycle into lead  168 . 
     Similarly, Line  7  shows the logical levels of the inc_even_slow signal, lead  134 , represented by cycles of one half of the LF frequency and line  8  shows the logical levels of inc_even_slow signal. Line  8  shows the output of even_clkd 1  of flip-flop  172  Q terminal into lead  173 , rising to logical high after a logical high of  134  and after rising HF clock signal. Line  9  shows the output of even_clkd 2  of flip-flop  174  Q terminal into lead  175 , delayed by one HF clock signal relative to even_clkd 1 , and line  10  depicts the even branch output even_cycle, lead  188 . Line  11  depicts the inc_fast output of conformational timer  160  into lead  192  of this inventive apparatus  100 . 
     Referring now to FIG. 3, depicting a block diagram  200  of an exemplary embodiment circuit for the conformational representation of signal  212  originating in a HF domain  202  and transmitted into a LF domain  209 . 
     The detailed embodiment of the circuit depends on the integer numbers N and m, defined by the relationships: 
     
       
           N=INT ( HF/LF )+1  (1) 
       
     
       m &gt;log 2 ( N )  (2) 
     Where N designates the number of the parallel output leads of Fast Signal Splitter  204  (FSS hereinbelow) for the splitting of signal  212  and the number m designates the number of output lines in bus  208 , m is preferably the smallest number satisfying relationship (2), or: 
     
       
           m=INT (log 2 ( N ))+1  (2a) 
       
     
     Bus  208  of m leads permits the log(2) representation in the LF domain of the number of HF cycles generated during one LF cycle duration. HF domain  202  also comprises of an output lead  211  of an HF clock (not shown). Also comprised in  202  is an N-outputs FSS  204  for the splitting of signal  212  into N outputs  221 ,  231 ,  241 ,  251 ,  261 , N equals five in this exemplary embodiment. Each one of said N outputs is applied to a corresponding module of N similar HF modules, designated respectively  220  through  260 . Each one of the outputs of said N HF modules is applied to a corresponding lead of N similar LF modules  320  through  360 , respectively. The N outputs of said LF modules are applied to LF counter  206 , generating in m-lined bus  208  a sequence of LF cycle-long binary representations of the number of HF cycle duration of signal  212  generated during each LF cycle. 
     Each one of the N HF modules  220  through  260  comprises a two-input XOR gate, numbered  222  through  262  in the respective modules, and an HF flip-flop, numbered  223  through  263  respectively, i.e. the HF flip-flop number equals the XOR gate number of its module increased by 1. The output of each group&#39;s XOR gate is applied to the D terminal of its respective HF flip-flop. 
     N LF modules, numbered  320  to  360  are provided and are connected to the Q outputs of HF flip-flops  223  to  263  by leads  225  through  265 , respectively. Each LF module comprises three serially connected LF flip-flops, first LF flip-flops numbered  321  to  361 , second LF flip-flops numbered  322  to  362  and third LF flip-flops numbered  323  to  363 , respectively. Also included are two-input LF modulo- 2  adders, which may be constituted by LF XOR gates numbered  324  to  364 , respectively. Lead  311  applies LF cycles to the clock terminal of any LF-clocked component. 
     The output of the Q terminal of each one of the respective HF flip-flops  223  through  263  is applied to the D terminal of the respective first LF flip-flops  321  to  361 , the outputs of the Q terminals of the first LF flip-flops are applied to the respective D terminals of the second LF flip-flops  322  to  362  and the outputs of the Q terminals of the second LF flip-flops are applied to respective D terminals of the third LF flip-flops  323  to  363  and to one input terminal of a respective two-input LF XOR gate  324  to  364 . The outputs of the Q terminals of the third LF flip-flops are applied to the respective second terminal of LF XOR gates  324  to  364 . The outputs of LF XOR gates  324  through  364  are applied in parallel through leads  325  through  365 , respectively, to N input terminals of adder  206 . Adder  206  outputs the number of input “1”&#39;s, representing the duration of signal  212 , expressed in number of HF cycles, by the binary output of the L lines of bus  208 . 
     FSS  204  outputs a round robin sequence of outputs of one HF cycle-length duration in N lines  223  through  263 , said outputs being staggered by one HF cycle length and generated as long as line  212  is “1” or logical high. Each one of the logical high outputs of lines  223  through  263  is applied to the D input terminal of first flip-flops  321  through  361 , whose Q terminal outputs are applied to the D input terminals of second flip-flops  322  through  362 . First and second flip-flops are provided due to signal stability, as is known. The Q terminal output of second flip-flops  322  through  362  is applied to one input terminal of modulo- 2  adders  324  through  364 , respectively. The Q terminal outputs of third LF flip-flops  323  to  363  is applied to the second input terminal of the respective LF XOR gates  324  to  364 . The output of the LF XOR gates is logical high if the exectly one output of the second and the third LF flip-flops is logical high, i.e. if a change in the logical levels of said flip-flops occurred during the one LF cycle duration corresponding to the HF signal output of the respective HF line. The logical output levels in bus  208  of adder  206  represent the number of HF cycles, during which line  212  was logically high, during one LF cycle. This number could be less than N or equal to N. For a line  212  logical high signal duration of P HF cycles, P being less than N. the output representation on bus  208  is P during one LF cycle. For a line  212  logical high signal duration of R HF cycles, R being equal to N, the output representation on bus  208  is N during one LF cycle. For a line  212  logical high signal duration of S HF cycles, S being higher than N, the output representation on bus  208  is N during the integer number T=INT(S/N) of T LF cycles, and equals to (P modulo N) during the next LF cycle. Thus a representation of the HF cycle duration of signal  212  is transmitted to the LF domain and is represented there by the output of adder  206 , as represented on bus  208 . 
     Referring now to FIG. 4, a block diagram  400  is depicted of an exemplary embodiment of a circuit for the conformational representation of signal  412  originating in a HE domain  402  and transmitted into a LF domain  409 . 
     The detailed embodiment of the circuit depends on the integer numbers N and m, defined as above by the relationships (1) applied to the values used in the embodiment of FIG.  4 : 
     
       
           N=INT (100/77.76)+1=2  (1) 
       
     
     
       
           m &gt;log 2 (2)  (2) 
       
     
     Where N designates the number of the parallel output leads of FSS  404  for the splitting of signal  412 , and the number m designates the number of output lines in bus  408  m is preferably the smallest number satisfying relationship (2), or: 
     
       
           m=INT (log 2 (2))+1=2  (2a) 
       
     
     Bus  408  of two leads or bits permits the log(2) representation in the 77.76 MHz LF domain of the number of 100 MHz HF cycles generated during one LF cycle duration. HF domain  402  also comprises of an HF lead  411  of an HF clock (not shown), applied to the clock terminals of HF components. 
     Also comprised in  402  is an N-outputs FSS  404 , N equals 2 in this exemplary embodiment, for the splitting of signal  412  into N outputs  421 ,  431 . Each one of outputs  421 ,  431 , is applied respectively to one of two similar HF modules  420 ,  430 . Each one of the outputs of said HF modules is applied to a corresponding lead of two LF modules  520 ,  530 , respectively. The two outputs of said LF modules are applied to LF adder  406 , generating in a 2-lined bus  408  a sequence of LF cycle-long binary representations of the number of HF cycle duration of signal  412  generated during each LF cycle. 
     Each one of HF modules com 420 ,  430 , comprises a two-input XOR gate, numbered  422 ,  432 , and an HF flip-flop, numbered  223 ,  233  respectively, i.e. the HF flip-flop number equals the XOR gate number of its module increased by 1. The output of each group&#39;s XOR gate is applied to the D terminal of its respective HF flip-flop. 
     Two LF modules, numbered  520  and  530  are provided, and are connected to the Q outputs of HF flip-flops  423 ,  433  via leads  424 ,  434 , respectively. Each LF module comprises three serially connected LF flip-flops, first LF flip-flops numbered  521 ,  531 , second LF flip-flops numbered  522  to  532  and third LF flip-flops numbered  523 ,  533 , respectively. Also included are two-input LF modulo- 2  adders, which may be constituted by LF XOR gates numbered  524 ,  534 , respectively. Lead  511  applies LF clock cycles to the clock terminals of LF components. 
     The output of the Q terminal of each one of the respective synchronizer HF flip-flops is applied to the D terminal of the respective first LF flip-flops  521 ,  531 , the outputs of the Q terminals of the first LF flip-flops are applied to the respective D terminals of second LF flip-flops  522 ,  532  and the outputs of the Q terminals of the second LF flip-flops are applied to respective D terminals of the third LF flip-flops  523 ,  533  and to one input terminal of a respective two-input LF XOR gate  524 ,  534 , The outputs of the Q terminals of the third LF flip-flops are applied to the respective second terminal of LF XOR gates  524 ,  534 , the outputs  525 ,  535  of said LF XOR gates are applied in parallel to N input terminals of adder  406 . Adder  406  outputs the number of input “1”, representing the duration of signal  412 , expressed in number of HF cycles, by the binary output of the m lines of bus  408 . 
     FSS  404  outputs a round robin sequence of outputs of one HF cyclelength duration in N=2 lines  421 ,  431 , said outputs being staggered by one HF cycle length and are generated as long as line  412  is “1” or logical high. The logical high outputs of flip-flops  423 ,  463 , tg_ 1 , tg_ 2  are applied via leads  424 ,  434 , respectively to the D input terminal of first flip-flops  521 ,  531 , whose Q terminal outputs are applied to the D input terminals of second flip-flops  522 ,  532 . First and second flip-flops are provided due to signal stability, as is known. The Q terminal output of second flip-flops  522  is applied to one input terminal of the two-input terminals of modulo- 2  adders, which may be constituted by XOR gates, and which are represented in this embodiment by LF XOR gates  524 ,  534 . The Q terminal outputs of third flip-flops  523 ,  533  is applied to the second input terminal of the respective LF XOR gates  524 ,  534 . The outputs of the LF XOR gates are logical high if only one output of the second and the third LF flip-flops is logical high, namely, if a change in the logical levels of said flip-flops occurred during the particular LF cycle duration corresponding to the HF signal output of the respective HF line. Line  408  represents the number of HF cycles during which line  412  was logically high throughout one LF cycle. This number could be less than N or equal to N. For a line  412  logical high signal duration of P HF cycles, P being less than N, the output representation on bus  408  is P during one LF cycle. For a line  412  logical high signal duration of R HF cycles, R being equal to N, the output representation on bus  408  is N during one LF cycle. For a line  412  logical high signal duration of S HF cycles, S being higher than N, the output representation on bus  408  is N during the integer number T=INT(S/N) of T LF cycles, and equals to (P modulo N) during the next LF cycle. Thus a representation of the HF cycle duration of signal  412 , is transmitted to the LF domain and is represented there by the output of adder  406 , as represented on bus  408 . 
     Referring now to FIG. 5 of timing diagrams of various electrical signals of another embodiment wherein N=2, line  1  shows the logical levels of the HF clock cycles, of 100.0 Mhz in this embodiment, and line  7  shows the logical levels of the LF clock cycles, of 77.76 Mhz in this embodiment. Full vertical lines mark the end of each LF cycle, while dotted vertical lines mark the end of each HF cycle. Line  2  shows the logical levels of signal  412 . Lines  3  and  4  show the logical levels of the inc_ 1  and inc_ 2  of leads  421  and  431  outputs respectively. Lines  5 , 6  show the logical levels of tg_ 1  and tg_ 2  of leads  423 ,  433 . Lines  8  and  10  show the output of tg_ 1 clkd 1  of Q terminal of flip-flop  521 , and of tg  1 clkd 2  of Q terminal of flip-flop  522 . Lines  9  and  11  show the output of tg_ 2 clkd 1 , tg_ 2 clkd 2  of the Q terminals of flip-flops  531 ,  532 . Lines  12  and  13  show the outputs of XOR gates  524 ,  534 , respectively, and line  14  shows the outputs of a two lines bus  408 . 
     Circuits constructed in accordance with the present invention may be particularly useful in communications applications, for example where signal transfer between different protocols may occur. Additionally, many processors may be comprised of several time domains and the present invention may enhance the efficiency of such processors and systems which use such processors, such as computer, networks, routers, servers, communications cards, and the like. 
     The preceding description of an exemplary embodiment is presented in order to enable a person of ordinary skill in the art to design, manufacture and utilize this invention. Various modifications and adaptations to the exemplary embodiment will be apparent to those skilled in the art, and different modifications may be applied to different embodiments. Therefore, it will be appreciated that the invention is not limited to what has been described hereinbelow merely by way of example. Rather, the invention is limited solely by the claims which follow this description.

Technology Classification (CPC): 7