Abstract:
An active terminator is configured with switches to select between terminating two lines for transmitting one differential signal pair or two single ended signals terminated in a pseudo-differential receiver. The receiver circuitry is configured with three differential comparators. One differential comparator receives both signal lines and other two differential comparators each receive one signal line and a reference voltage. The signal lines are terminated in a resistive voltage divider with electronic switches coupling the positive and ground voltages. The top and bottom nodes of the resistor divider in both terminators are cross-coupled with pass gates. In the pseudo-differential mode the pass gates are OFF and the electronic switches are ON with known resistances. In the differential mode, the electronic switches are OFF and the pass gates are ON with known resistances. The pass gate and switch resistances are sized with the resistors to insure a desired termination impedance.

Description:
TECHNICAL FIELD 
   The present invention relates in general to board level transmission line drivers and receivers, and in particular, to references for differential and pseudo-differential drivers and receivers. 
   BACKGROUND INFORMATION 
   Digital computer systems have a history of continually increasing the speed of the processors used in the system. As computer systems have migrated towards multiprocessor systems, sharing information between processors and memory systems has also generated a requirement for increased speed for the off-chip communication networks. Designers usually have more control over on-chip communication paths than for off-chip communication paths. Off-chip communication paths are longer, have higher noise, impedance mismatches, and have more discontinuities than on-chip communication paths. Since off-chip communication paths are of lower impedance, they require more current and thus more power to drive. 
   When using inter-chip high-speed signaling, noise and coupling between signal lines (cross talk) affects signal quality. One way to alleviate the detrimental effects of noise and coupling is through the use of differential signaling. Differential signaling comprises sending a signal and its compliment to a differential receiver. In this manner, noise and coupling affect both the signal and the compliment equally. The differential receiver only senses the difference between the signal and its compliment as the noise and coupling represent common mode signals. Therefore, differential signaling is resistant to the effects that noise and cross talk have on signal quality. On the negative side, differential signaling increases pin count by a factor of two for each data line. The next best thing to differential signaling is pseudo-differential signaling. Pseudo-differential signaling comprises comparing a data signal to a reference voltage using a differential receiver or comparator. 
   When high speed data is transmitted between chips, the signal lines are characterized by their transmission line parameters. High speed signals are subject to reflections if the transmission lines are not terminated in an impedance that matches the transmission line characteristic impedance. Reflections may propagate back and forth between driver and receiver and reduce the margins when detecting signals at the receiver. Some form of termination is therefore usually required for all high-speed signals to control overshoot, undershoot, and increase signal quality. Typically, a Thevenin&#39;s resistance (equivalent resistance of the Thevenin&#39;s network equals characteristic impedance of transmission line) is used to terminate data lines allowing the use of higher valued resistors. Additionally, the Thevenin&#39;s network is used to establish a bias voltage between the power supply rails. In this configuration, the data signals will then swing around this Thevenin&#39;s equivalent bias voltage. When this method is used to terminate data signal lines, a reference voltage is necessary to bias a differential receiver that operates as a pseudo-differential receiver to detect data signals in the presence of noise and cross talk. 
   Sometimes pseudo-differential signaling is not adequate for a desired signal quality and true differential signaling is needed at the expense of reduced bandwidth. The signal lines for pseudo-differential signaling are individually terminated to eliminate reflections. Typically a voltage divider provides a bias voltage as well as generating the proper impedance level by the parallel combination of the resistors in the voltage divider. In a true differential receiver, the termination resistance is usually placed across the two signal lines. Configuring a communication network so that either differential or pseudo-differential signaling could be used with a termination network that was switchable would lead to excessive capacitive loading unless a novel approach was used. Therefore, there is a need for a switch selectable termination system that enables both true differential and pseudo-differential signaling while minimizing capacitive loading. 
   SUMMARY OF THE INVENTION 
   A communication network is configured as signal pairs with the two signal lines terminated in a switch selectable termination network. The individual signal lines are each coupled to the positive input of a pseudo-differential comparator which has the negative input coupled to a reference voltage. Each of the signal lines are terminated in the common node of a resistor voltage divider that has its positive and negative nodes coupled to the positive and negative power supply voltages, respectively, with electronic switches. The positive nodes of the voltage divider terminators are cross-coupled with pass gates to the corresponding negative nodes. In this manner, two data signals may be transmitted and received using pseudo differential signaling. If true differential signaling is required, then the electronic switches are turned OFF and the pass gates are gated ON with a known resistance. This results in the voltage divider resistors being coupled in series with a pass gate and in parallel across the two signal lines. The parallel combination of the resistances is sized to correctly terminate the differential lines. The electronic switches are sized with the voltage divider resistors to provide the required pseudo terminating resistance and the pass gates are sized so that the series/parallel combination of the pass gates and the voltage divider resistors provides the required differential terminating resistance. 
   The foregoing has outlined rather broadly the features and technical advantages of the present invention in order that the detailed description of the invention that follows may be better understood. Additional features and advantages of the invention will be described hereinafter which form the subject of the claims of the invention. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
     For a more complete understanding of the present invention, and the advantages thereof, reference is now made to the following descriptions taken in conjunction with the accompanying drawings, in which: 
       FIG. 1  is a circuit diagram of prior art pseudo-differential signaling; 
       FIG. 2  is a circuit diagram of differential signaling; 
       FIG. 3A  is a circuit diagram illustrating the termination of a pseudo differential signal line to ground; 
       FIG. 3B  is a circuit diagram illustrating the termination of a pseudo differential signal line to the positive supply voltage; 
       FIG. 3C  is a circuit diagram illustrating voltage divider termination of a pseudo differential signal line; 
       FIG. 4  is a circuit diagram of across line termination of differential signal lines; 
       FIG. 5  is a circuit diagram of two signal lines simultaneously coupled to a pseudo-differential comparator circuit and to a differential comparator; 
       FIG. 6  is a circuit diagram illustrating a termination network suitable to switch between differential and pseudo-differential signaling; 
       FIG. 7  is a circuit diagram illustrating a termination network suitable to switch between differential and pseudo-differential signaling according to embodiments of the presenting invention; and 
       FIG. 8  is a block diagram of a data processing system suitable for using embodiments of the present invention. 
   

   DETAILED DESCRIPTION 
   In the following description, numerous specific details are set forth to provide a thorough understanding of the present invention. However, it will be obvious to those skilled in the art that the present invention may be practiced without such specific details. In other instances, well-known circuits may be shown in block diagram form in order not to obscure the present invention in unnecessary detail. For the most part, details concerning timing considerations and the like have been omitted inasmuch as such details are not necessary to obtain a complete understanding of the present invention and are within the skills of persons of ordinary skill in the relevant art. 
   Refer now to the drawings wherein depicted elements are not necessarily shown to scale and wherein like or similar elements are designated by the same reference numeral through the several views. 
     FIG. 1  is a circuit diagram of typical pseudo-differential signaling for transmitting data from drivers in a Chip A  140  to receivers in a Chip B  142  via a transmission path  141 . Drivers  101 ,  102  and  114  represent three of a number of n drivers sending data to receivers  110 ,  113  and  116 , respectively. Exemplary driver  101  receives data  0   120  and generates an output that swings between power supply rail voltages P 1   103  (logic one) and G 1   104  (logic zero). When the output of driver  101  is at P 1   103 , any noise on the power bus is coupled to transmission line  105  along with the logic state of the data signal. Exemplary transmission line  105  is terminated with a voltage divider comprising resistors  108  and  109 . Receiver input  130  has a DC bias value determined by the voltage division ratio of resistors  108  and  109  and the voltage between P 2   106  and G 2   107 . Receiver  110  is powered by voltages P 2   106  and G 2   107  which may have different values from P 1   103  and G 1   104  due to distribution losses, noise coupling, and dynamic impedance of the distribution network. Exemplary receiver  110  is typically a voltage comparator or high gain amplifier that amplifies the difference between a signal at input  130  and a reference voltage Vref  117 . Voltage reference Vref  117  may be programmable and generated by a variety of techniques. 
     FIG. 2  is a circuit diagram of true differential signaling. Data in  201  is coupled to a differential driver  210  that generates a digital signal  203  and the complement of the digital signal  202 . These two signals are transmitted over transmission lines  204  and  205 . A differential receiver  209  has a positive input receiving signal  206  and a negative input receiving complementary signal  207 . Signals  206  and  207  are shown with analog features of overshoot, undershoot, and ringing consistent with effects seen when transmission paths are not ideal. Receiver  209  converts the differential signals back to a digital signal  208  whose signal quality and characteristics are dependent on the amount of distortion experienced by signals  206  and  207  and the ability of differential receiver  209  to reject common mode variations. 
     FIG. 3A  is a circuit diagram of a pseudo-differential receiver  301  where signal node  304  is terminated to ground potential  305  with resistor  303 . A signal on node  304  is compared to Vref  302  and pseudo-differential receiver  301  generates a detected output at node  310 . 
     FIG. 3B  is a circuit diagram of a pseudo-differential receiver  301  where signal node  304  is terminated to positive voltage potential  306  with resistor  303 . A signal on node  304  is compared to Vref  302  and pseudo-differential receiver  301  generates a detected output at node  310 . The high frequency impedance between positive voltage potential  306  and ground potential  305  is considered low enough that the circuit configurations  FIG. 3A  and  FIG. 3B  are considered to have equivalent termination impedances. 
     FIG. 3C  is a circuit diagram of a pseudo-differential receiver  301  where signal node  304  is terminated in a voltage divider comprising resistors  307  and  308  between positive voltage potential  306  and ground potential  305 . A signal on node  304  is compared to Vref  302  and pseudo-differential receiver  301  generates a detected output at node  310 . Resistors  307  and  308  are sized so their parallel combination is equivalent to resistor  303 . Resistors  307  and  308  set a bias potential (e.g., one half of positive voltage potential  306 ) at node  304 . Again, the high frequency impedance between positive voltage potential  306  and ground potential  305  is considered low enough that the circuit configurations  FIG. 3A ,  3 B and  FIG. 3C  may have the equivalent termination impedances. 
     FIG. 4  is a circuit diagram of a differential receiver  401  having a positive input  404  coupled to signal Data  1   402  and a negative input  403  coupled to complementary signal Data _ 1   403 . Resistor  406  is coupled between inputs  403  and  404  to set the differential termination impedance (shown as 50 ohms). 
     FIG. 5 . is a circuit diagram illustrating two data channels or paths that may be used to transmit one differential signal or two single ended signals. If Data  0   501  and Data  1   509  are independent data signals, then the outputs  505  and  513 , respectively, of pseudo-differential receivers  504  and  512  may be enabled to generate corresponding detected data signals. If Data  0   501  and Data  1   509  are complementary data signals, then the output  508  of differential receiver  507  may be enabled to generate a corresponding detected data signal. Thus, transmission lines  503  and  511  either transmit a single differential data signal or two independent data signals. Output nodes  514  and  515  are coupled to all three receivers and gating (not shown) would be used to steer the desired detected signal to down-stream logic. 
     FIG. 6 . is a circuit diagram of two data channels that are switch selectable for use as true differential or pseudo-differential signaling according to embodiments of the present invention. For true differential signaling, differential receiver  602  with output  605  is used and for two channel pseudo-differential signaling, receivers  601  and  603  coupled to Vref  608  generate detected signals at outputs  604  and  606 . Data  0   624  and Data  1   621  may correspond to a single differential signal or may correspond to two independent data signals. Depending on which mode is desired, the termination network may be altered using control signals  622  and  623  to provide the best signal quality. Data  0   624  is terminated in a voltage divider network comprising resistors  610  and  611  and transistors  609  and  612 . Likewise, Data  1   621  is terminated in a voltage divider network comprising resistors  616  and  618  and transistors  617  and  619 . When pseudo-differential signals is desired, control signal  623  is set to a logic zero and control signal  622  is set to a logic one turning ON transistors  609 ,  612 ,  617 , and  619  while turning OFF pass gate  614 . This action couples resistors  610 ,  611 ,  616 , and  618  to the signal lines and opens the connection between resistors  613  and  615  removing them from the data signal lines. In the differential mode, control signal  623  is a logic one and control signal  622  is a logic zero which turns OFF transistors  609 ,  612 ,  617 , and  619  and turns ON pass gate  614 . Even though the gating the transistors alters the resistive portion of the terminating impedance for signals Data  0   624  and Data  1   621 , it does nothing to alter the capacitive loading resulting from the physical structure of resistors  610 - 611 ,  613 ,  615 - 616  and  618 . The circuitry of  FIG. 6  does provide a termination network that is switchable between true differential and pseudo-differential, however, its performance would suffer and may be inadequate for some high frequency signaling applications. 
     FIG. 7  is a circuit diagram of two data channels that are switch selectable for use as true differential or pseudo-differential signaling according to another embodiment of the present invention. As explained relative to  FIG. 6 , Data  0   713  and Data  1   721  may correspond to a single differential signal or may correspond to two independent data signals. Pseudo differential receivers  722  and  727  compare independent data signals at inputs  710  and  718 , respectively, to Vref  719  and generate independent detected data signals at outputs  723  and  717 . Likewise, differential receiver  725  amplifies the difference between a differential signal between inputs  715  and  716  to generate a detected data signal at output  724 . Depending on which mode (pseudo-differential or true differential) was desired, the outputs  723  and  717  or  724  may be enabled for use by down-stream logic (not shown). 
   Inputs  710  and  715  are coupled to signal Data  0   713  and inputs  718  and  716  are coupled to signal Data  1   721 . Only resistors  709 ,  711 ,  706  and  708  are directly coupled to these inputs and thus their parasitic capacitance is lower than the termination network in  FIG. 6 . Transistors  702 ,  712 ,  705  and  707  along with pass gates  703  and  704  are then used to determine the circuit configuration of resistors  709 ,  711 ,  706  and  708 . In the pseudo-differential mode, resistors  709 ,  711 ,  706  and  708  are configured as voltage dividers between the positive and ground voltage potentials and in the differential mode they are configured to appear as a resistive load across inputs  715  and  716 . 
   In the pseudo-differential mode, control signal  720  is set to a logic one and control signal  726  is set to a logic zero. Control signal  726  turns ON the P channel field effect transistors (PFET)  712  and  705  coupling the positive supply voltage to resistors  706  and  711 . Likewise control signal  720  turns ON NFETs  707  and  702  coupling the ground potential to resistors  708  and  709 . Since control signal  726  is coupled to the NFETs in pass gates  703  and  704  and control signal  720  is coupled to the corresponding PFETs, pass gates  703  and  704  are gated OFF. The pseudo-differential mode insures that one voltage divider (resistors  711  and  709 ) configuration appears at inputs  710  and  715  and the other voltage divider (resistors  706  and  708 ) appears at inputs  716  and  718 . Gating circuitry (not shown) is used to direct outputs  717  and  723  to down-stream logic. 
   Since the PFETs  712  and  705  appear in series with resistors  711  and  706  and the NFETs  702  and  707  appear in series with resistors  708  and  709 , their resistance may be sized to ensure a desired value when gated ON by control signals  720  and  726  in the pseudo-differential mode. Likewise, pass gates  703  and  704  have devices sized to ensure a desired termination resistance value for the series/parallel combination of resistors  709 ,  711 ,  706 , and  708  in the true differential mode. For an exemplary network providing a 50 ohm single ended termination and a 100 ohm differential termination, resistors  709 ,  711 ,  706 , and  708  are set to 75 ohms, PFETs  712  and  705  and NFETs  702  and  707  are configured to have an ON resistance of 25 ohms, and pass gates  703  and  704  are configured to have an ON resistance of 50 ohms. 
   In the true differential mode, control signal  720  is set to a logic zero and control signal  726  is set to a logic one. Control signal  726  turns OFF PFETs  712  and  705  decoupling the positive supply voltage from resistors  706  and  711 . Likewise control signal  720  turns OFF NFETs  707  and  702  decoupling the ground potential from resistors  708  and  709 . Since control signal  726  is coupled to the NFETs in pass gates  703  and  704  and control signal  720  is coupled to the corresponding PFETs, pass gates  703  and  704  are gated ON. The pseudo-differential mode ensures that resistors  711  and  708  are coupled in series and in parallel with the series connection of resistors  706  and  709 . The series/parallel resistor combination now appears across inputs  710  and  718  and  715  and  716 . Since the power supply voltages are decoupled from the resistors, the true differential termination is purely passive. Gating circuitry (not shown) is used to direct which output  724  to down-stream logic. The circuit configuration of  FIG. 7  provides switch selectable termination for pseudo-differential and true differential signaling while minimizing capacitive loading thus improving high frequency performance. 
     FIG. 8  is a high level functional block diagram of a representative data processing system  800  suitable for practicing the principles of the present invention. Data processing system  800  includes a central processing system (CPU)  810  operating in conjunction with a system bus  812 . System bus  812  operates in accordance with a standard bus protocol, such as the ISA protocol, compatible with CPU  810 . CPU  810  operates in conjunction with electronically erasable programmable read-only memory (EEPROM)  816  and random access memory (RAM)  814 . Among other things, EEPROM  816  supports storage of the Basic Input Output System (BIOS) data and recovery code. RAM  814  includes, DRAM (Dynamic Random Access Memory) system memory and SRAM (Static Random Access Memory) external cache. I/O Adapter  818  allows for an interconnection between the devices on system bus  812  and external peripherals, such as mass storage devices (e.g., a hard drive, floppy drive or CD/ROM drive), or a printer  840 . A peripheral device  820  is, for example, coupled to a peripheral control interface (PCI) bus, and I/O adapter  818  therefore may be a PCI bus bridge. User interface adapter  822  couples various user input devices, such as a keyboard  824  or mouse  826  to the processing devices on bus  812 . Exemplary display  838  may be a cathode ray tube (CRT), liquid crystal display (LCD) or similar conventional display units. Display adapter  836  may include, among other things, a conventional display controller and frame buffer memory. Data processing system  800  may be selectively coupled to a computer or telecommunications network  841  through communications adapter  834 . Communications adapter  834  may include, for example, a modem for connection to a telecom network and/or hardware and software for connecting to a computer network such as a local area network (LAN) or a wide area network (WAN). CPU  810  and other components of data processing system  800  may contain logic circuitry in two or more integrated circuit chips that are separated by a significant distance relative to their communication frequency so that terminated transmission lines are needed to insure performance. Some of these lines may need to be switch selectable between true differential and pseudo-differential signaling improve reliability and thus need to have a corresponding termination network that is likewise switch selectable according to embodiments of the present invention to minimize performance degradation due to capacitive loading. 
   Although the present invention and its advantages have been described in detail, it should be understood that various changes, substitutions and alterations can be made herein without departing from the spirit and scope of the invention as defined by the appended claims.