Abstract:
A method for channel estimation in an Orthogonal Frequency Division Multiplexing (OFDM) system, including: a transmitter determining a distribution density of pilot OFDM symbols according to the maximum Doppler frequency shift supported by the system, and transmitting pilot OFDM symbols and data OFDM symbols based on the distribution density of the pilot OFDM symbols; a receiver estimating frequency-domain channel information of the data OFDM symbols according to the received pilot OFDM symbols. The invention solves the problem of a large performance loss at a high-delay channel and a system with rapidly varying channel. The invention offers a better performance of channel estimation while the channel environment is varying rapidly, enhances the performance of a high-delay channel, makes a data communication system more suitable to a changing environment and makes better performance to the practical channel estimation, so that the data transmission efficiency of the system is increased.

Description:
This is a continuation of International Application No. PCT/CN2005/000757 filed May 30, 2005, which claims the benefit of Chinese Patent Application No. 200410042935.2 filed Jun. 1, 2004, the entire respective disclosures of which are hereby incorporated herein by reference. 

   BACKGROUND OF THE DISCLOSURE 
   1. Field of the Invention 
   The invention relates to Orthogonal Frequency Division Multiplexing (OFDM) techniques, and, more specifically, relates to a method and a device for channel estimation in an OFDM system. 
   2. Background of the Invention 
   The OFDM technique is one of the frequency division multiplexing techniques for high rate data transmission services. Compared with traditional single carrier techniques, the OFDM provides higher spectrum efficiency by using simple equalization algorithm. Meanwhile, it is unnecessary to allocate frequency guard bands between adjacent subcarriers to avoid frequency interferences, which is adopted in the traditional Frequency Division Multiplexing (FDM), so that the bandwidth is saved. 
   Recently, the OFDM technique is widely used in the communications system, and has been applied in the wireless LAN standard 802.11a and the fixed wireless access standard 802.16a. Besides, regarding the wireless access network of 3GPP and the physical layer of IEEE 802.20, the OFDM technique is being considered for constructing mobile wireless access system with higher spectrum efficiency. 
     FIG. 1  shows a networking diagram of a typical frequency multiplexing cellular system. In this system, two Radio Network Controllers (RNC), RNC 1  and RNC 2 , are connected to the Core Network (CN); some Base Stations (BS) are connected to one of the two RNCs: BS 1 , BS 2  and BS 3  connecting to RNC 1 , while BS 4 , BS 5  and BS 6  connecting to RNC 2 ; two Mobile Stations (MS), MS 1  and MS 2 , keep wireless connections with these BSs.  FIG. 2  is a typical cell omnidirectional antenna multiplexing mode, or succinctly called cell multiplexing mode.  FIG. 3  is a typical cell 120 degrees directional antenna multiplexing mode, or briefly called sectored multiplexing mode. A data transmission system using OFDM technique has the following advantages: 
   1. Good robustness under multipath delay spread. As shown in  FIG. 4 , a time-domain OFDM symbol includes two parts: a data part and a cyclic prefix part; the cyclic prefix part is generated by circulating the last portion of the data part; as shown in the diagram the data part occupies a duration T data  and the cyclic prefix part occupies a duration T cp . The robustness of the OFDM technique refers to that: comparing with an OFDM symbol duration T s , a typical channel impulse response duration is quite short and occupies only a quite short part of the T s , so by increasing a shorter cyclic prefix, i.e. the T cp , the interference between signals caused by multipath is completely eliminated. 
   2. Good robustness under frequency selective fading. Through redundant solutions such as channel coding, the OFDM technique can recover the digital signal carried by a badly fading subcarrier. 
   3. Simple equalization algorithm. The OFDM technique transmits the signal in the frequency domain and simple multiplications can be used to express channel effects in the frequency domain, so that a simple one tap equalizer could be used to equalize the signal in the OFDM system. 
   4. Higher spectrum efficiency comparing with the commonly used FDM technique. 
   Although the data transmission system utilizing OFDM technique has the above advantages, in order to realize the advantages in a practical system, and more importantly, to make the OFDM system work normally, it is necessary to develop several key technologies including: frequency synchronization, symbol synchronization, frame synchronization, channel estimation and equalization etc. These key technologies relate not only to application environment of the system but also to requirements on the network configuration of the system. 
   The purpose of the channel estimation in the above key technologies is that: through the channel estimation, the receiver can obtain the frequency domain information of the channel on which the transmitter transmits the data; based on the frequency domain information of the channel, the receiver can make equalization processing to obtain the data. Therefore, the channel estimation is an important precondition for the receiver to obtain the data correctly and efficiently. 
   IEEE 802.11a protocol provides a channel estimation technology. The frame structure of an 802.11a system is shown in  FIG. 5 . Every frame includes a preamble and a data OFDM symbol with uncertain length. The data OFDM symbol includes user data and signaling. The pilot subcarrier allocation solution of 802.11a is shown in  FIG. 6 . In the physical layer selection solution of 802.11a and 802.16a, the channel estimation uses the preamble. Specifically, the receiver knows the date carried in every subcarrier of the preamble transmitted by the transmitter, so that with the received preamble, the channel condition of every subcarrier of the preamble can be obtained; when the channel environment varies slowly, the channel condition of the subcarriers of the preamble could be considered as the channel condition of the corresponding subcarriers of the OFDM symbol. 
   In other words, the channel estimation solution provided by 802.11a is based on that channel condition of the data OFDM symbol is approximate to the channel condition of the corresponding preamble. When the channel environment varies rapidly, this approximation will make greater errors. Besides, the channel environment also varies due to the relative movement between the receiver and transmitter. So the above solution is not effective while being applied in the system with rapidly varying channel environment. The channel condition in the current mobile wireless communication system varies rapidly, so obviously the channel estimation solution provided by 802.11a is not suitable for the mobile wireless communication system. 
   Although in the 802.11a, pilot subcarriers are introduced to trace the variety of the channel so as to amend the channel condition of the subcarriers of the preamble, and to take the amended channel condition of the subcarriers of the preamble as the channel condition of the subcarriers of the data OFDM symbol, the amend can not reflect the rapid variety of the channel condition and will still cause a considerable degradation in the performance. 
   In order to solve the disadvantages mentioned above, a pilot subcarrier allocation solution of time-frequency grid is proposed by the art and shown in  FIG. 7 . In this solution, the pilot OFDM symbol, i.e. the preamble, is evenly distributed on the time-frequency plane. Utilizing the pilot OFDM symbol to trace the variety of the channel can partially solve the problem of varying channel. 
   The SIEMENS Corporation has proposed to the 3GPP RAN1 a proposal Tdoc R1-030780 about a specific solution for allocating the pilot frequency with the time-frequency grid mode, as well as the channel estimation method and the simulation result. The solution uses twice-order one-dimension interpolation to obtain the data subcarrier channel condition on the time-frequency plane: first making third-order Lagrange interpolation on the time-domain, and then making seventh-order Lagrange interpolation on the frequency-domain. The simulation result provided by SIEMENS shows that: comparing the ideal channel estimation, the channel estimation solution of SIEMENS has 0.5-0.7 dB performance degradation for the PA3, PB3 and VA30 channels and even has floor error at BLER=0.13 for the VB30 channel. This means that for channels with large delays, the channel estimation solution of SIEMENS makes large performance degradations. 
   SUMMARY OF THE INVENTION 
   In view of the above, the invention provides a method for the channel estimation in the OFDM system in order to reduce the performance degradation at the receiver while making channel estimation. 
   The invention also provides a transmitter and a receiver for the channel estimation in the OFDM system in order to reduce performance degradation at the receiver while making channel estimation. 
   According to a method for channel estimation in an Orthogonal Frequency Division Multiplexing (OFDM) system, a transmitter determines a distribution density of pilot OFDM symbols according to the maximum Doppler frequency shift supported by the system, and transmits pilot OFDM symbols and data OFDM symbols based on the distribution density of the pilot OFDM symbols; and a receiver estimates frequency-domain channel information of the data OFDM symbols according to the received pilot OFDM symbols. 
   An Orthogonal Frequency Division Multiplexing (OFDM) transmitter includes a pilot OFDM symbol distribution density determining module, used for determining a distribution density of the pilot OFDM symbol according to the maximum Doppler frequency shift supported by an OFDM system, whose input is the maximum Doppler frequency shift and output is connected to a pilot OFDM symbol and data OFDM symbol generating and transmitting module; the pilot OFDM symbol and data OFDM symbol generating and transmitting module, used for generating the pilot OFDM symbol and the data OFDM symbol according to the distribution density of the pilot OFDM symbol determined by the pilot OFDM symbol distribution density determining module, and for transmitting the pilot OFDM symbol and the data OFDM symbols. 
   An Orthogonal Frequency Division Multiplexing (OFDM) receiver includes a channel equalization module and a data channel estimation module, wherein the data channel estimation module includes: a pilot OFDM symbol time-domain channel response calculating module, used for obtaining time-domain channel response at a pilot OFDM symbol according to a received time-domain pilot OFDM symbol, and for outputting the time-domain channel response at the pilot OFDM symbol to a pilot OFDM symbol time-domain channel information calculating module; the pilot OFDM symbol time-domain channel information calculating module, used for calculating time-domain channel information of the pilot OFDM symbol according to the time-domain channel response at the pilot OFDM symbol, and for outputting the time-domain channel information of the pilot OFDM symbol to a data OFDM symbol frequency-domain channel information calculating module; and the data OFDM symbol frequency-domain channel information calculating module, used for calculating frequency-domain channel information of the data OFDM symbol according to the time-domain channel information of the pilot OFDM symbol, and for outputting the calculated frequency-domain channel information to the channel equalization module. 
   In accordance with the solution provided by the invention, the distribution density of the pilot OFDM symbol may be determined according to the maximum Doppler frequency shift supported by the OFDM system, and the receiver estimates the data OFDM symbol frequency domain channel information according to the received pilot OFDM symbol. In this way, better performance can be achieved at a high-delay and rapidly varying channel environment. The invention enhances the channel environment adaptability of the data communication system, improves the performance of the practical channel estimation in the OFDM system, and increases the data transmission efficiency of the system. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
       FIG. 1  is a networking diagram illustrating a typical frequency multiplexing cellular system. 
       FIG. 2  is a schematic diagram illustrating a typical cell omnidirectional antenna mode. 
       FIG. 3  is a schematic diagram illustrating a typical cell 120 degrees sector antenna mode. 
       FIG. 4  is a diagram illustrating an OFDM symbol. 
       FIG. 5  is a diagram illustrating a frame in 802.11a. 
       FIG. 6  is a schematic diagram illustrating pilot frequency distribution in 802.11a. 
       FIG. 7  is a schematic diagram illustrating the pilot frequency grid mode. 
       FIG. 8  is a schematic diagram illustrating a distribution relationship between the pilot OFDM symbol and the data OFDM symbol. 
       FIG. 9  is a schematic diagram illustrating a structure of the pilot OFDM symbol. 
       FIG. 10  is a schematic diagram illustrating a structure of the data OFDM symbol. 
       FIG. 11  is a flowchart illustrating the process of a transmitter transmitting OFDM symbols. 
       FIG. 12  is a flowchart illustrating the process of a receiver receiving OFDM symbols. 
       FIG. 13  is a schematic diagram illustrating a number section of OFDM symbols in accordance with the invention. 
       FIG. 14  is a schematic diagram illustrating a course of channel estimation in the receiver in accordance with an embodiment of the invention. 
       FIG. 15  is a flowchart illustrating a process of channel estimation corresponding to  FIG. 14 . 
       FIG. 16  is a flowchart illustrating another process of channel estimation. 
       FIG. 17  is a simulation diagram of channel estimation performance under Vehicle A channel, 30 kmph and truncation path of 32. 
       FIG. 18  is a simulation diagram of channel estimation performance under Vehicle A channel, 60 kmph and truncation path of 32. 
       FIG. 19  is a simulation diagram of channel estimation performance under Vehicle B channel, 30 kmph and truncation path of 160. 
   

   DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
   The invention first sets a distribution density of the pilot OFDM symbol according to the maximum Doppler frequency shift supported by the system; based on the distribution density of the pilot OFDM symbol, the transmitter transmits the pilot OFDM symbol and data OFDM symbol; then the receiver makes the channel estimation of the data OFDM symbol according to the received pilot OFDM symbol. 
   In the following, the invention will be described in detail with reference to accompanying drawings and embodiments. 
   First, the distribution density of the pilot OFDM symbol is determined according to the maximum Doppler frequency shift, i.e. the moving speed of the mobile station, supported by the system. Similar to the prior art, the frame structure in accordance with the embodiments of the invention includes the pilot OFDM symbol and the data OFDM symbol, as shown in  FIG. 8 . To determine the distribution density of the pilot OFDM symbol is to determine the number of the data OFDM symbol between adjacent pilot OFDM symbols. The number of the data OFDM symbol between adjacent pilot OFDM symbols depends on how rapidly the channel environment varies. More specifically, supposing that the relation between the maximum Doppler frequency shift f d,max  supported by the system and the maximum moving speed v max  supported by the system is: 
   
     
       
         
           
             f 
             
               d 
               , 
               max 
             
           
           = 
           
             
               f 
               c 
             
             · 
             
               v 
               c 
             
           
         
       
     
   
   Wherein, f c  is the carrier frequency of the system, and c is the velocity of light. Generally speaking, the number of the data OFDM symbol between adjacent pilot OFDM symbols should meet the following condition: 
   
     
       
         
           
             
               n 
               · 
               
                 T 
                 d 
               
               · 
               
                 f 
                 
                   d 
                   , 
                   max 
                 
               
             
             &lt; 
             
               
                 1 
                 2 
               
               ⁢ 
               
                 i 
                 . 
                 e 
                 . 
               
             
           
           , 
           
             
               n 
               · 
               
                 T 
                 d 
               
               · 
               
                 f 
                 c 
               
               · 
               
                 v 
                 c 
               
             
             &lt; 
             
               
                 1 
                 2 
               
               . 
             
           
         
       
     
   
   Wherein T d  is the duration occupied by the data OFDM symbol; and n is the number Of the data OFDM symbol between adjacent pilot OFDM symbols. 
   It is the same with the prior art that the length of the pilot OFDM symbol can be equal or unequal to the length of the data OFDM symbol. Similarly, it is the same with the prior art that both the pilot OFDM symbol and the data OFDM symbol include a cyclic prefix part and a data part; the cyclic prefix part is generated by cycling the last portion of the data part. The length of the cyclic prefix part is expressed as the number of its sample point; and the length of the data part is expressed as the number of its sample points, too. The structure of the pilot OFDM symbol is shown in  FIG. 9 ; wherein the N p,cp  is the length of the cyclic prefix part, and the N p,data  is the length of the data part. The structure of the data OFDM symbol is shown in  FIG. 10 ; wherein the Nd d,cp  is the length of the cyclic prefix part, and the N d,data  is the length of the data part. 
   Usually, the length of the data part in the pilot OFDM symbol can be equal or unequal to the length of the data part in the data OFDM symbol. In order to save the system resource occupied by the pilot OFDM symbol, the solution in accordance with the embodiment of the invention sets the data part length of the pilot OFDM symbol N p,data  shorter than the data part length of the data OFDM symbol N d,data . In general, the two values N p,data  and N d,data  can be set to satisfy the following formula: 
   
     
       
         
           
             
               N 
               
                 p 
                 , 
                 data 
               
             
             = 
             
               
                 1 
                 
                   2 
                   n 
                 
               
               · 
               
                 N 
                 
                   d 
                   , 
                   data 
                 
               
             
           
           , 
           
             
               wherein 
               ⁢ 
               
                   
               
               ⁢ 
               n 
             
             = 
             0 
           
           , 
           
             1 
             ⁢ 
             … 
           
         
       
     
   
   Usually the length of the cyclic prefix part of the pilot OFDM symbol can be equal or unequal to the length of the cyclic prefix part of the data OFDM symbol. In order to enhance the negative effect to the pilot OFDM symbol caused by the multipath delay, the solution in accordance with the embodiment of the invention sets the length of the cyclic prefix part of the pilot OFDM symbol N p,cp  longer than the length of the cyclic prefix part of the data OFDM symbol N d,cp . 
   Based on the above settings of the pilot OFDM symbol and the data OFDM symbol, while transmitting, first the transmitter generates the pilot OFDM symbol and the data OFDM symbol according to the cyclic prefix part and the data part of the pilot OFDM symbol and the data OFDM symbol, then multiplexes these two symbols on the time-domain, and transmits the generated OFDM symbol after the processes such as D/A converting. The transmitting procedure is shown in  FIG. 11 . 
   While receiving, first the receiver samples the received electromagnetism signal, then de-multiplexes the sampled data on the time-domain based on the obtained time synchronization to form the time-domain pilot OFDM symbol and the time-domain data OFDM symbol; and then obtains the pilot OFDM symbol and the data OFDM symbol on the frequency-domain; and then estimates the frequency-domain channel information of the data OFDM symbol based on the pilot OFDM symbol; and finally uses channel equalization based on the frequency-domain channel information of the data OFDM symbol to recover the data OFDM symbol transmitted. The receiving procedure is shown in  FIG. 12 . 
   During the course of handling the received signal, while making estimation of the frequency-domain channel information of the data OFDM symbol based on the pilot OFDM symbol, the receiver could adopt two solutions besides the existing solution. The first is as follows: the receiver first obtains the time-domain channel information of the pilot OFDM symbol based on the received pilot OFDM symbol; then with the interpolation algorithm, estimates the time-domain channel information of the data OFDM symbol according to the time-domain channel information of the pilot OFDM; and then with the time-domain channel information of the data OFDM symbol, obtains the frequency-domain channel information of the data OFDM symbol. The second method is as follows: first the receiver obtain the time-domain channel information of the pilot OFDM symbol based on the received pilot OFDM symbol; but then obtains the frequency-domain channel information of the pilot OFDM symbol based on the time-domain channel information of the pilot OFDM symbol; and then with the interpolation algorithm, estimates the frequency-domain channel information of the data OFDM symbol according to the frequency-domain channel information of the adjacent pilot OFDM symbol. 
   In order to describe these two processing ways, numbers are assigned to the transmitted OFDM symbol with the following rules: 
   The number of the pilot OFDM symbol: the number of the pilot OFDM symbol is assigned according to the transmitting time sequence, and the pilot OFDM symbol that is transmitted earlier takes a smaller number; 
   The natural number of the n data OFDM symbols between adjacent pilot OFDM symbols: taking the natural number from 1 to n, wherein the data OFDM symbol that is transmitted earlier takes a smaller number; 
   The number of the data OFDM symbol: first, multiply the number of the pilot OFDM symbol that is adjacent but transmitted earlier than the data OFDM symbol with the number of the data OFDM symbols between the adjacent pilot OFDM symbols, and then add the natural number of the data OFDM symbol between adjacent pilot OFDM symbols. 
   With the above rules, a portion of the OFDM symbol number is shown in  FIG. 13 . Wherein, k−1, k, k+1 and k+2 are pilot OFDM symbol numbers, n*(k−1)+1 . . . , n*(k−1)+n are the numbers of the data OFDM symbols between the pilot OFDM symbol k−1 and the pilot OFDM symbol k; n*k+1 . . . , n*k+n are the numbers of the data OFDM symbols between the pilot OFDM symbol k and the pilot OFDM symbol k+1; n*(k+1)+1 . . . , n*(k+1)+n are the numbers of the data OFDM symbols between the pilot OFDM symbol k+1 and the pilot OFDM symbol k+2. 
   Based on the above rules, supposing that the i th  subcarrier of the k th  pilot OFDM symbol carries a frequency-domain signal D k,i , then the k th  pilot OFDM symbol carries frequency-domain signal sequence (D k,0 , D k,1 , . . . , D k,N     p,data   ). 
   The first channel estimation method, according to which the time-domain data OFDM symbol channel information is obtained first, and then the frequency-domain channel information thereof is obtained, will be described in detail in the following.  FIG. 14  shows the processing diagram of the first solution and  FIG. 15  shows the flowchart. 
   Step  1501 . According to the received time-domain pilot OFDM symbol, the time-domain channel response at the pilot OFDM symbol is obtained. 
   Supposing that the time-domain signal sequence of the received k th  pilot OFDM symbol is (S k,0 ′, S k,1 ′, . . . , S k,N     p,data   ′), through Fourier transform such as Fast Fourier Transform (FFT), the received frequency-domain signal sequence (D k,0 ′, D k,1 ′, . . . , D k,N     p,data   ′) a is obtained. Since the frequency-domain signal sequence carried by the k th  pilot OFDM symbol is (D k,0 , D k,1 , . . . , D k,N     p,data   ), the frequency-domain channel response at the k th  pilot OFDM symbol is 
             (         D     k   ,   0     ′       D     k   ,   0         ,       D     k   ,   1     ′       D     k   ,   1         ,   …   ⁢           ,       D     k   ,     N     p   ,   data         ′       D     k   ,     N     p   ,   data               )     ,         
briefly (C k,0   p , C k,1   p , . . . , C k,N     p,data     p ) By making inverse Fourier-transform such as Inverse Fast Fourier Transform (IFFT) to the obtained frequency-domain channel response (C k,0   p , C k,1   p , . . . , C k,N     p,data     p ), the time-domain channel response at the k th  pilot OFDM symbol is obtained, briefly (c k,0   p , c k,1   p , . . . , c k,N     p,data     p ).
 
   Step  1502 . According to the time-domain channel response at the pilot OFDM symbol, the time-domain channel information of the pilot OFDM symbol is extracted; the time-domain channel information includes path delay, path fading etc. 
   Having obtained the time-domain channel response at the pilot OFDM symbol, in order to reduce channel noises and interference, it is necessary to analyze the information to obtain the effective channel information. 
   There are two methods to obtain the effective channel information: one is a simple truncation method, which may be used when the range of the channel delay of the wireless transmission environment is known; another is an adaptive extracting method of the channel information. 
   For the simple truncation method, the truncation range is determined based on the delay spread supported by the system. For example, supposing that the maximum channel delay is N sample points, then the time-domain channel response at the pilot OFDM symbol (c k,0   p , c k,1   p , . . . , c k,N     p,data     p ), obtained at Step  1502 , is directly truncated, and the truncation range is a little bit larger than the corresponding sample points of the maximum delay; for example, the truncation range is N′, then N′≧N. In this case, the obtained time-domain channel at the k th  pilot OFDM symbol is (c k,0   p , c k,1   p , . . . , c k,N′   p , 0, . . . , 0), wherein the number of zero is N p,data −N′. For the adaptive extracting method, the most powerful paths among the time-domain channel response (c k,0   p , c k,1   p , . . . , c k,N     p,data     p ) of the pilot OFDM symbols, which is continuously received at a period of time from the time-domain channel response, is selected as the effective paths, wherein the selected paths need not to be continuous. For example, in a period of time, the (c k,i     0     p , c k,i     1     p , . . . , c k,i     M     p ) can be selected as the effective channel information for the period of time. Having determined the effective channel information, the zero is used to substitute the non-selected time-domain channel value in the time-domain channel response of the pilot OFDM symbol. 
   Besides, the adaptive extracting method mentioned above can be simplified. For example, truncation can be taken in the method, so as to form an adaptive truncation method. The adaptive truncation method is as follows: first determining the truncation length N′ by analyzing the continuous time-domain channel response (c k,0   p , c k,1   p , . . . , c k,N     p,data     p ) at the pilot OFDM symbol in order to find the energy concentrated area and taking the length of the area as N′; then obtaining the time-domain channel value before N′ and substituting the unselected time-domain channel response at the pilot OFDM symbol, i.e. the time-domain channel value after N′, with zero. In this way, the time-domain channel information is determined. 
   Step  1503 . Estimate the time-domain channel information of the data OFDM symbol by taking a specific interpolation to the time-domain channel information of the adjacent pilot OFDM symbols. 
   Having obtained the time-domain channel information of the pilot OFDM symbol (c k,0   p , c k,1   p , . . . , c k,N′   p , 0, . . . , 0) the time-domain channel information of the data OFDM symbol (c s,0   d , c s,1   d , . . . , c s,N′   d , 0, . . . , 0) is estimated, wherein s is the number of the data OFDM symbol. 
   Specifically, the c k*n+j,i   d  value can be estimated by using the ( . . . , c k−1,i   p , c k,i   p , c k+1,i   p , c k+2,i   p , . . . ), wherein j is the natural number of the data OFDM symbols between the adjacent pilot OFDM symbols. 
   To estimate the value, a (2 l−1) th -order Lagrange interpolation can be adopted. The typical estimation formula is: 
             c         k   *   n     +   j     ,   i     d     =       ∑     m   =       -   l     +   1       l     ⁢       c       k   +   m     ,   i     p     ·     (     1       (       ∏     q   =   1       l   -   m       ⁢   q     )     ·     (       ∏     q   =       -   l     +   m   -   m         -   l       ⁢   q     )         )     ·     (         ∏     q   =       -   l     +   1       l     ⁢     (       j     n   +   1       -   q     )         (       j     n   +   1       -   m     )       )               
wherein the c k+m,i   p  the time-domain channel value at the i th  sample point of the (k+m) th  pilot OFDM symbol, and c k*n+j,i   d  is the time-domain channel value at the i th  sample point of the (k*n+j) th  data OFDM symbol, and n is the number of data OFDM symbols between the adjacent pilot OFDM symbols.
 
   When first-order Lagrange interpolation, i.e. linear interpolation, is adopted, the above formula is simplified to: 
   
     
       
         
           
             c 
             
               
                 
                   k 
                   * 
                   n 
                 
                 + 
                 j 
               
               , 
               i 
             
             d 
           
           = 
           
             
               c 
               
                 k 
                 , 
                 i 
               
               p 
             
             + 
             
               
                 j 
                 
                   n 
                   + 
                   1 
                 
               
               · 
               
                 ( 
                 
                   
                     c 
                     
                       
                         k 
                         + 
                         1 
                       
                       , 
                       i 
                     
                     p 
                   
                   - 
                   
                     c 
                     
                       k 
                       , 
                       i 
                     
                     p 
                   
                 
                 ) 
               
             
           
         
       
     
   
   Wherein c k,i   p  the time-domain channel value at the i th  sample point of the k th  pilot OFDM symbol, and c k*n+j,i   d  is the time-domain channel value at the i th  sample point of the (k*n+j) th  data OFDM symbol, and n is the number of data OFDM symbols between the adjacent pilot OFDM symbols. 
   It may also use (2 l−1) th -order the logarithmic Lagrange interpolation, the typical estimation formula is: 
   
     
       
         
           
             ln 
             ⁡ 
             
               ( 
               
                 c 
                 
                   
                     
                       k 
                       * 
                       n 
                     
                     + 
                     j 
                   
                   , 
                   i 
                 
                 d 
               
               ) 
             
           
           = 
           
             
               ∑ 
               
                 m 
                 = 
                 
                   
                     - 
                     l 
                   
                   + 
                   1 
                 
               
               l 
             
             ⁢ 
             
               
                 ln 
                 ⁡ 
                 
                   ( 
                   
                     c 
                     
                       
                         k 
                         + 
                         m 
                       
                       , 
                       i 
                     
                     p 
                   
                   ) 
                 
               
               · 
               
                 ( 
                 
                   1 
                   
                     
                       ( 
                       
                         
                           ∏ 
                           
                             q 
                             = 
                             1 
                           
                           
                             l 
                             - 
                             m 
                           
                         
                         ⁢ 
                         q 
                       
                       ) 
                     
                     · 
                     
                       ( 
                       
                         
                           ∏ 
                           
                             q 
                             = 
                             
                               
                                 - 
                                 l 
                               
                               + 
                               m 
                               - 
                               m 
                             
                           
                           
                             - 
                             l 
                           
                         
                         ⁢ 
                         q 
                       
                       ) 
                     
                   
                 
                 ) 
               
               · 
               
                 ( 
                 
                   
                     
                       ∏ 
                       
                         q 
                         = 
                         
                           
                             - 
                             l 
                           
                           + 
                           1 
                         
                       
                       l 
                     
                     ⁢ 
                     
                       ( 
                       
                         
                           j 
                           
                             n 
                             + 
                             1 
                           
                         
                         - 
                         q 
                       
                       ) 
                     
                   
                   
                     ( 
                     
                       
                         j 
                         
                           n 
                           + 
                           1 
                         
                       
                       - 
                       m 
                     
                     ) 
                   
                 
                 ) 
               
             
           
         
       
     
   
   wherein the c k+m,i   p  is the time-domain channel value at the i th  sample point of the (k+m) th  pilot OFDM symbol, and c k*n+j,i   d  is the time-domain channel value at the i th  sample point of the (k*n+j) th  data OFDM symbol, and n is the number of data OFDM symbols between the adjacent pilot OFDM symbols. 
   Similarly, when first-order logarithmic Lagrange interpolation, i.e. linear logarithmic Lagrange interpolation is adopted, the above formula is simplified to: 
   
     
       
         
           
             ln 
             ⁡ 
             
               ( 
               
                 c 
                 
                   
                     
                       k 
                       * 
                       n 
                     
                     + 
                     j 
                   
                   , 
                   i 
                 
                 d 
               
               ) 
             
           
           = 
           
             
               ln 
               ⁡ 
               
                 ( 
                 
                   c 
                   
                     k 
                     , 
                     i 
                   
                   p 
                 
                 ) 
               
             
             + 
             
               
                 j 
                 
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               · 
               
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                     ⁡ 
                     
                       ( 
                       
                         c 
                         
                           
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                           i 
                         
                         p 
                       
                       ) 
                     
                   
                   - 
                   
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                       ( 
                       
                         c 
                         
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   wherein the c k,i   p  is the time-domain channel value at the ith sample point of the (k+m)th pilot OFDM symbol, and the c k*n+j,i   d  is the time-domain channel value at the i th  sample point of the (k*n+j) th  data OFDM symbol, and n is the number of data OFDM symbols between the adjacent pilot OFDM symbols. 
   With anyone of the above formulas, the (c s,0   d , c s,1   d , . . . , c s,N′   d ) value is estimated; after adding N d,data −N′ of zeros to follow it, the (c s,0   d , c s,1   d , . . . , c s,N′   d , 0, . . . , 0) is obtained. 
   Step  1504 . With the time-domain channel information of the data OFDM symbol, the frequency-domain channel information of the data OFDM symbol can be obtained. 
   Specifically, the frequency-domain channel response at the s th  data OFDM symbol (C s,0   d , C s,1   d , . . . , C s,N     d,data     d ) is obtained by taking IFFT to the obtained time-domain channel response at the sth data OFDM symbol (c s,0   d , c s,1   d , . . . , c s,N′   d , 0, . . . , 0). 
   According to the second channel estimation method, first the frequency-domain channel information of the pilot OFDM symbol is obtained, and the frequency-domain channel information of the data OFDM symbol is obtained. The flowchart is shown in  FIG. 16  with the following steps: 
   Step  1601 . According to the received time-domain pilot OFDM symbol, the time-domain channel response at the pilot OFDM symbol is obtained. 
   This step is the same as Step  1501 . 
   Step  1602 . According to the time-domain channel response at the pilot OFDM symbol, the time-domain channel information of the pilot OFDM symbol is extracted; the time-domain channel information includes the path delay, the path fading, etc. 
   This step is the same as Step  1502 . 
   Step  1603 . The corresponding frequency-domain channel information of the pilot OFDM symbol is obtained according to the obtained time-domain channel information of the pilot OFDM symbol. 
   Step  1604 . The frequency-domain channel information of the data OFDM symbol is estimated by taking interpolation to the frequency-domain channel information of the pilot OFDM symbol. 
   In Step  1604 , the interpolation is the (2 l□1) th -order Lagrange interpolation. Besides, the frequency-domain channel information of the data OFDM symbol may be obtained without interpolation, but by directly taking the frequency-domain channel information of the pilot OFDM symbol as the frequency-domain channel information of the data OFDM symbol that is adjacent to the pilot OFDM symbol. 
   The solution in accordance with the invention has better performance in channel environments that are rapidly varying and that have a high delay. Specifically, comparing with the ideal channel estimation, when the truncation path number is 32, for the channel estimation of Vehicle A channel with 30 kmph the performance loss is less than 0.3 dB, which is shown in  FIG. 17 ; when the truncation path number is 32, for the channel estimation of Vehicle A channel with 60 kmph the performance loss is less than 1.1 dB, which is shown in  FIG. 18 ; even when the truncation path number is 160, for the channel estimation of Vehicle B channel with 30 kmph the performance loss is less than 0.7 dB, which is shown in  FIG. 9 . 
   The foregoing description is only the preferred embodiments of the present invention and is not to be used for limiting the invention, and that various other changes, equal substitutions and modifications without departing from the scope and spirit of the invention are intended to be included within the scope of the present invention.