Abstract:
A method for controlling a step down regulator includes (a) generating a first feedback signal as a function of the voltage at the output node; (b) generating a second feedback signal as a function of the voltage at the input node; (c) maintaining the on-time of the low-side switch at a fixed duration; and (d) varying the on-time of the high-side switch to be proportional to the first feedback signal and inversely proportional to the second feedback signal so that the switching frequency of the high and low side switches is approximately constant.

Description:
BACKGROUND OF THE INVENTION 
     Switching regulators are intended to be efficient machines for converting an input voltage to an output voltage. The two most common types of switching regulators are Boost (voltage increasing converters) and Buck (voltage decreasing regulators). Both Boost and Buck regulators are very important for battery powered applications such as cellphones. As shown in  FIG. 1A , a traditional implementation for a Buck regulator includes a switch M 1  connected between an input voltage (V BATT  in this case) and a node V X . A diode D is connected between the node V X  and ground. An inductor L is connected between V X  and the output node (V OUT ) of the regulator. A filtering capacitor connects V OUT  to ground. The node V OUT  is also connected to a load (not shown). 
     A control circuit turns switch M 1  on and off in a repeating pattern. This causes the Buck regulator to have two distinct operational phases. In the first phase, shown in  FIG. 1B , the switch M 1  is on. During this phase, called the charging phase, the inductor is connected between the battery and the output node V OUT . This causes current to flow from the battery to the load. In the process energy is stored in the inductor L in the form of a magnetic field. 
     In the second, or discharge phase the switch M 1  is opened (see  FIG. 1C ). In this phase the diode and inductor are connected in series between ground and the load. In this phase, current supplied by the inductor&#39;s magnetic field flows to the output node V OUT  and the load. As the inductor&#39;s magnetic field collapses and the voltage over the inductor falls, the diode prevents current flowing through the inductor from reversing direction and flowing from the load to ground. 
     In general, switching regulators work in environments where both the input and output voltage are dynamic voltages. Input voltages change as battery voltages decline over time or as other components draw more power. Output voltages change depending on load requirements. Switching regulators react to changes in input and output voltages by varying the amount of time that the switch M 1  remains on. This is done using two different methods. In the first method, the switching frequency is varied—as the load on the regulator increases (relative to its supply) the switching frequency is increased. This is known as pulse frequency modulation or PFM. In the second method a fixed switching frequency is used and the amount of time that the switch M 1  is turned on is varied. For larger loads, the switches stay on longer. This is known as pulse width modulation of PWM. Of the two methods, PWM is often preferred because it produces noise at a known and therefore filterable fixed frequency. Filtering the noise created by a PFM regulator can be problematic—especially in portable applications. 
     The regulator architecture just illustrated suffers one fundamental flaw: the diode D has, by nature a forward voltage drop. Depending on the type of diode, this can be fairly small, but is still generally unacceptable for low voltage applications. For this reason, it is common to replace the diode D with a second switch M 2 .  FIG. 2  shows a Buck regulator of this type. 
     The basic idea is that the switch M 2  operates with no voltage drop (when switched on) overcoming the disadvantages inherent in diode based designs. Regulators of this type are often referred to as “synchronous regulators” because the two switches are driven synchronously—when one is on, the other is off. In the real world, this is never quite the case. It takes time to turn the switches on and off and control cannot be done with absolute precision. For this reason, the act of turning a switch off is always done slightly in advance of the act of turning the other switch on. This technique, known as break-before-make or BBM avoids the situation where both switches are on at the same time and power is connected to ground (a condition known as shoot through). 
     Switching regulators fall into two categories; voltage-mode and current-mode. Generally, voltage-mode regulators are easy to implement, but with the requirement of more complex control-loop compensation. Current-mode regulators are typically more difficult to implement, but have simplified control loop compensation. 
    
    
     
       SUMMARY OF THE INVENTION 
       BRIEF DESCRIPTION OF THE DRAWINGS 
         FIG. 1A  is a block diagram of a prior art buck switching regulator. 
         FIG. 1B  is a block diagram showing the prior art buck switching regulator of  FIG. 1  during the charge phase of operation. 
         FIG. 1C  is a block diagram showing the prior art buck switching regulator of  FIG. 1  during the discharge phase of operation. 
         FIG. 2  is a block diagram of a prior art buck switching regulator that includes a low-side switch. 
         FIG. 3A  is a block diagram of a buck type switching regulator as provided by the present invention. 
         FIG. 3B  is a block diagram of a buck type switching regulator as provided by the present invention. 
     
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     The disclosed invention includes a current-mode pseudo fixed frequency control method for step-down switching regulators. The control method is generally applicable to the type of switching regulator shown in  FIG. 1A  and described previously. When operating in steady state with continuous inductor current, regulators of this type exhibit the following property: 
             D   =         t   ON       T   SW       =         t   ON     *     f   SW       ≈       V   OUT       V   IN                 
Where:
         D is the duty cycle,   t ON  is the high-side switch on-time,   T SW  is the switching period,   f SW  is the switching frequency,   V OUT  is the output voltage, and   V IN  is the input voltage.
 
One result of this property is that controlling t ON  to be proportional to V OUT  and inversely proportional to V IN  causes f SW  to be approximately constant. The disclosed control method takes advantage of this result to produce an approximately constant switching frequency whenever the inductor current is continuous. When the load current decreases sufficiently, the inductor current becomes discontinuous, causing the switching frequency to decrease. This is desired, since efficiency at light load is improved by lower switching frequency.
       

       FIG. 3A  shows a step-down regulator  300  implemented to use the pseudo fixed frequency control method. Regulator  300  uses a resistive voltage divider (R 1  and R 2 ) to generate a feedback voltage (V FB ) that is less than and proportional to the output voltage (V OUT ). A transresistance or current sense amplifier  302  is used to measure the current passing through low side MOSFET M 2  and inductor L when MOSFET M 2  is switched on. Current sense amplifier  302  produces an output voltage referred to as the current sense voltage (V CS ). The feedback voltage (V FB ) and the current sense voltage (V CS ) are summed together using a summer  304  and applied to the input of a first voltage comparator  306 . A reference voltage is applied to the other input of first comparator  304 . In many cases, it may be desirable to implement summer  304  and comparator  306  as a single device. 
     The output of first comparator  304  is applied to one input of an AND gate  308 . The output of AND gate  308  is connected to trigger an on-time one-shot  310 . On-time one-shot  310  is also connected to receive as feedback the output voltage V OUT  and input voltage V IN  of regulator  300 . The output of on-time one-shot  310  is connected to high-side switch M 1  and shoot-through protection circuit  312 . Shoot-through protection circuit  312  is connected, in turn to low-side switch M 2 . The output of on-time one-shot  310  is also connected to the input of an off-time one-shot  314 . The output of off-time one-shot  314  provides the second input to AND gate  308 . 
     During operation, first comparator  306  monitors the difference between the 1) sum of the feedback voltage V FB  and the current sense voltage V CS  and 2) the reference voltage. When the sum of the feedback voltage V FB  and the current sense voltage V CS  drops below the reference voltage, the output of first comparator  306  changes state and triggers on-time one-shot  310 . The output of on-time one-shot  310  causes high-side switch M 1  to turn on for a period of time equal to the period of on-time one-shot  306 . That period is set by circuitry within on-time one-shot  31   0  to be proportional to V OUT  and inversely proportional to V IN . At the end of that time period, the output of on-time one-shot  310  changes states causing high-side switch M 1  to turn off and low-side switch M 2  to turn on. Shoot-through protection circuit  312  ensures that there is a delay between the turning off of high-side switch M 1  and the turning on of low-side switch M 2  preventing the input voltage from being coupled to ground through the two switches. 
     The change in state of on-time one shot  310  triggers off-time one-shot  314 . The active-low output of off-time one-shot  314  ensures that the output of AND gate  308  is held low. This ensures that the output of first comparator  306  is prevented from triggering on-time one-shot  310  for at least the period of off-time one-shot  314 . For this reason, each switching cycle of regulator  300  includes a minimum off time (where switch M 1  is off and switch M 2  is on) equal to the period of off-time one-shot  314 . It should be noted, however that the off-time may exceed this minimum since the next switching cycle does not occur until comparator  306  detects that the sum of the feedback voltage V FB  and the current sense voltage V CS  has once again dropped below the reference voltage. 
     As stated above, the presented control method switches at an approximately constant frequency only in steady-state. When regulator  300  encounters a load current transient at the output, the switching frequency changes to quickly adjust the current through the inductor and the voltage across the capacitor improving transient response. After the inductor current and capacitor voltage have changed to their new steady-state values, regulator  300  returns to approximately the same constant switching frequency. Because the frequency is allowed to change slightly, the presented control method does not require slope compensation as is normally required for current-mode regulators, easing the implementation of such a DC to DC converter regulator. 
       FIG. 3B  shows an alternate implementation of step-down regulator  300  that is configured so that the feedback to one-shot  310  comes from V IN  only. This differs from the previously described implementation where the one-shot  310  receives feedback from both V IN  and V OUT . This change somewhat simplifies the implementation of step-down regulator  300 . At the same time, the modification shown in  FIG. 2C  has the result that the switching frequency of step-down regulator  300  would change whenever the output voltage V OUT  is not regulating (e.g., start-up or overload conditions).