Abstract:
Disclosed are circuits and methods of identifying defective memory cells among rows and columns of memory cells. In one embodiment, all the memory cells in an array are programmed to conduct with a conventional read voltage applied and not to conduct with a conventional read-inhibit voltage applied. Any rows that conduct with the read-inhibit voltage applied are termed “leaky,” and are defective. Another read-inhibit voltage lower than the conventional level is selected to cause even leaky cells not to conduct. This test read-inhibit voltage is consecutively applied to each row under test. If one of the rows includes a leaky bit, that bit will conduct with the conventional read-inhibit voltage applied but will not conduct with the test read-inhibit voltage applied. The test flow therefore identifies a row as including a leaky bit when a leak is suppressed by application of the test read-inhibit voltage. A redundant row can be provided to replace a row having a leaky bit.

Description:
FIELD OF INVENTION 
     The invention relates generally to methods and circuits for identifying a defective memory cell in an array of memory cells. 
     BACKGROUND 
     Conventionally, non-volatile semiconductor memory structures with high levels of integration (e.g., EPROM, EEPROM, flash EPROM, and the like) suffer from high defect rates. A significant percentage of defects common to non-volatile memory produce so-called “leaky” memory cells, which lead to memory misreads, greatly depressing memory yield. 
     FIG.  1 ( a ) (prior art) depicts a configurable memory cell  100 , including a storage transistor T 1 . Storage transistor T 1  includes a floating gate  115 , a control gate  117  connected to a wordline  120 , a drain terminal  125  connected to a bitline  130 , and a source terminal  135  connected to a ground terminal. During a programming operation, different voltages are applied to wordline  120  and bitline  130  causing electron tunneling from floating gate  115  to drain  125 . This transfer of negative charge from floating gate  115  decreases the threshold voltage of storage transistor T 1  (to a programmed threshold voltage V THP ). During an erase operation, different voltages are applied to wordline  120  and bitline  130  causing electron tunneling from drain  125  to floating gate  115 , the reverse of the programming process. This transfer of negative charge to floating gate  115  increases the threshold voltage of storage transistor T 1  (to an erased threshold voltage V THE ). 
     To read memory cell  100 , a read voltage V R  is applied to wordline  120 . The threshold voltage V THP  of a programmed cell is less than the read voltage V R , SO transistor T 1  conducts with read voltage V R  applied to control gate  117  if memory cell  100  is programmed; in contrast, the threshold voltage V THE  of an erased cell is above the read voltage V R , so transistor T 1  does not conduct with read voltage V R  applied to wordline  120  if memory cell  100  is erased. Whether a given cell conducts with the read voltage applied to the control gate is therefore indicative of the program state of the cell. In the following examples, the programmed state corresponds to a logic-zero state (a “logic zero”) and the erased state corresponds to a logic-one state (a “logic one”). 
     FIG.  1 ( b ) (prior art) depicts a memory array  150  including N rows and M columns of memory cells  100 . Each row of memory array  150  includes M storage transistors T 1  with their respective control gates connected to one wordline. For example, all M control gates of storage transistors T 1  in a first row are connected to a first wordline WL&lt;1&gt;. Each column of memory array  150  includes N storage transistors T 1  with their respective drain terminals connected to one bitline. For example, all N drain terminals of storage transistors T 1  in a first column are connected to a first bitline BL&lt;1&gt;. 
     As discussed above in connection with FIG.  1 ( a ), programming and erasing memory cells  100  of memory array  150  includes applying appropriate voltages on the M wordlines and N bitlines. Program and erase voltages are chosen so that all memory cells  100  in memory array  150  exhibit a nominal programmed threshold voltage V THP  and a nominal erased threshold voltage V THE . The nominal values of programmed and erased threshold voltages V THP  and V THE  determine the appropriate read voltage V R  value used during a read operation. 
     During a read operation, all bitlines are pre-charged to a relatively high voltage representative of a logic one. Then read voltage V R  is applied to a selected wordline WL&lt;K&gt; while a read-inhibit voltage V RI  less than the programmed threshold voltage V THP  is applied to all unselected wordlines (i.e., the control gates of the cells-within memory array  150  not being read). Thus biased, only programmed memory cells on the selected wordline WL&lt;K&gt; will conduct, pulling respective bitlines to a low voltage level representative of a logic zero; and neither programmed nor erased cells on all unselected wordlines conduct. 
     Memory array  150  can have one or more defective memory cells. A memory cell is “defective” if its electrical characteristics are outside of an acceptable range. For example, a leaky memory cell exhibits a programmed threshold voltage V THP  that is substantially less than required. If the programmed threshold voltage V THP  of a given memory cell is below the read-inhibit voltage V RI , that memory cell will “leak” when not selected, causing the associated column to read a logic zero regardless of whether a programmed or erased cell is selected. 
     Modern memory circuits include spare rows or columns of memory cells that can be substituted for respective rows or columns that include defective cells. It can be difficult, however, to precisely locate some types of defects. For example, a leaky memory cell affects an entire column, making it difficult to single out the defective cell. Replacing the defective column solves the problem in many instances; however, redundant rows are preferred for some memory architectures, so it may be important to identify the defective row. Moreover, even in the absence of redundant rows or columns, identifying defective memory cells aids in troubleshooting manufacturing processes. There is therefore a need for circuits and methods for identifying individual defective memory cells. 
     SUMMARY 
     The present invention is directed to circuits and methods for identifying defective memory cells in memory arrays. In one embodiment, all the memory cells in an array are programmed to conduct with a conventional read voltage applied and not to conduct with a conventional read-inhibit voltage applied. Any rows that conduct with the read-inhibit voltage applied are termed “leaky,” and are defective. Another read-inhibit voltage lower than the conventional level is selected to cause even leaky cells not to conduct. This test read-inhibit voltage is consecutively applied to each row under test. If one of the rows includes a leaky bit, that bit will conduct with the conventional read-inhibit voltage applied but will not conduct with the test read-inhibit voltage applied. The test flow therefore identifies a row as including a leaky bit when a leak is suppressed by application of the test read-inhibit voltage. A redundant row can be provided to replace a row having a leaky bit. 
     In one embodiment, a memory array includes a test row and some wordline select logic. During a test operation, the wordline select logic simultaneously applies three wordline voltages, a pair of read-inhibit voltages V RI1  and V RI2  and a read voltage V R , to wordlines in the memory-cell array. The first wordline voltage V RI1  is an unusually low read-inhibit voltage of a level selected to insure that even leaky cells will not conduct. The second and third wordline voltages V RI2  and VR are conventional read-inhibit and read voltages, respectively. 
     In a test method in accordance with one embodiment, each memory cell is erased (i.e., is configured to exhibit a relatively high erased threshold voltage V THE ). Each row other than the test row is then programmed (i.e., is configured to exhibit a relatively low programmed threshold voltage V THP ). The wordline select logic then applies the conventional read voltage V R  to the wordline of the test row. Being erased, the memory cells in the test row do not conduct. At the same time, the wordline select logic applies the low read-inhibit voltage VRI 1  to the wordline associated with one of the rows under test and applies the conventional read-inhibit voltage V RI2  to the remaining wordlines. 
     The read voltage on the test-row wordline is less than the erased threshold voltage, so the memory cells in the test row are biased off and will not conduct. The first read-inhibit voltage is less than the programmed threshold voltage, so low in fact that even leaky cells will not conduct. Thus, the memory cells within the associated row will not conduct even if leaky. Finally, the second read-inhibit voltage will prevent properly working programmed memory cells from conducting, but is insufficient to render leaky memory cells nonconductive. Thus biased, any conduction in the memory array indicates that one of the memory cells with the second read-inhibit voltage applied is leaking. 
     The first read-inhibit voltage is consecutively applied to each row under test. If one of the rows includes a leaky bit, that bit will conduct in every case except when the first read-inhibit voltage is applied to the leaky cell. The test flow therefore identifies a row as including a leaky bit when a leak is suppressed by application of a relatively strong read-inhibit voltage. Once a defective bit is identified, the row address of the leaky cell is stored for later consideration. Some embodiments include redundant rows, which can be substituted for row containing defective bits. 
     The allowed claims, and not this summary, define the scope of the invention. 
    
    
     BRIEF DESCRIPTION OF THE FIGURES 
     FIG.  1 ( a ) (prior art) is a diagram of a memory cell. 
     FIG.  1 ( b ) (prior art) is a diagram of an N-by-M memory array. 
     FIG. 2 is a block diagram of a memory circuit. 
     FIG. 3 is a flow chart of a test method identifying a defective memory cell. 
     FIG. 4 a block diagram of an ISC memory assembly with redundancy row capability. 
     FIG. 5 is a detailed block diagram of a wordline select circuit. 
     FIG.  6 ( a ) is a detailed block diagram of a top decoder. 
     FIG.  6 ( b ) is a detailed circuit diagram of a two-stage voltage level shifter circuit. 
     FIG.  7 ( a ) is a detailed block diagram of row decoder. 
     FIG.  7 ( b ) is a detailed block diagram of a row driver. 
     FIG.  7 ( c ) is a detailed circuit diagram of a wordline driver. 
     FIG.  7 ( d ) is a detailed circuit diagram of a wordline multiplexer. 
    
    
     DETAILED DESCRIPTION 
     FIG. 2 depicts a memory circuit  200  in accordance with one embodiment of the invention. Memory circuit  200  includes a memory block  220  that conventionally includes an array of memory cells  270  arranged in a plurality of rows  260  and columns  265 . Each memory cell  270  is the same or similar to memory cell  100  of FIG.  1 ( a ). Memory circuit  200  additionally includes a test row  280  and a wordline select circuit  250  connected to rows  260  and  280  via a plurality of respective wordlines WL&lt;1:N&gt; and WLT. Wordline select circuit  250  is adapted to simultaneously apply three wordline voltages V RI1 , V RI2 , and VR to memory block  220  to support test methods that identify individual defective memory cells. The following example assumes a leaky memory cell  270 A for illustrative purposes. 
     FIG. 3 depicts a flow chart  300  illustrating a method of testing memory circuit  200  of FIG. 2 to identify defective memory cells (e.g., leaky memory cell  270 A in the example). The following discussion employs memory circuit  200  in conjunction with flow chart  300 . 
     Beginning with step  305 , each memory cell  270  within memory block  220  is erased (i.e., is configured to exhibit an erased threshold voltage V THE ). Next, in step  310 , each row except test row  280  is programmed (i.e., is configured to exhibit a programmed threshold voltage V THP ) In the following sequence of steps, the contents of test row  280  are read with each of the remaining rows  260  inhibited. 
     As with a normal read operation, bitlines BL&lt;1:M&gt; are pre-charged to a level representative of a logic one (step  315 ). In step  325 , wordline select circuit  250  simultaneously applies: 
     1. a read voltage V R  to test row  280  via test wordline WLT; 
     2. a first read-inhibit voltage V RI1  to one of rows  260  to be tested for leaky bits (e.g., wordline WL&lt;K−1&gt;); and 
     3. a second read-inhibit voltage V RI2  to the remaining wordlines (e.g., wordlines WL&lt;1&gt; through WL&lt;K−2&gt; and WL&lt;K&gt; through WL&lt;N&gt;). 
     Read voltage V R  is greater than programmed threshold voltage V THP  but less than erased threshold voltage V THE . Thus, memory cells in test row  280  are off and do not affect the logic state of the pre-charged bitlines. First read-inhibit voltage V RI1  is less than programmed threshold voltage V THP , and is selected to be sufficiently low that even leaky cells will not conduct with read-inhibit voltage V RI1  applied on the respective wordline; thus, memory cells in the row  260  to which first read-inhibit voltage V RI1  is applied do not conduct even if leaky. Second read-inhibit voltage V R12  is a conventional read-inhibit voltage; thus, memory cells in the rows  260  to which read-inhibit-voltage V RI2  is applied conduct if leaky but do not otherwise conduct. In one embodiment, read voltage V R  is three volts, programmed threshold voltage V THP  is about zero to 1.5 volts, erased threshold voltage is about 4 to 6 volts, second read-inhibit voltage V RI2  is negative two volts, and first read-inhibit voltage V RI1  is negative four volts. 
     Next, in step  330 , the logic states of bitlines BL&lt;1:M&gt; are examined with the three wordline voltages applied. Any logic zeroes indicate the presence of a leaky memory cell among the cells to which read-inhibit voltage V RI2  is applied. In the illustration of FIG. 2, defective memory cell  270 A is provided with a read-inhibit voltage V RI2  insufficient to turn off leaky memory cell  270 A, so bitline BL&lt;M−1&gt; is pulled down to a low logic level, indicating an error. Due to the resulting mismatch between the level provided on bitline BL&lt;M−1&gt; and the expected correct level, wordline select circuit  250  selects the next wordline WL&lt;K&gt; for application of read-inhibit voltage V RI  (step  340 ) and the process returns to step  315 . 
     Steps  315  through  330  are repeated, this time with first read-inhibit voltage V RI1  applied to wordline WL&lt;K&gt;, the wordline associated with leaky memory cell  270 A. Because read-inhibit voltage V RI1  is low enough to render a leaky cell non-conductive, bitline BL&lt;M−1&gt; will no longer produce an error. The test flow therefore indicates that the relatively low read-inhibit voltage V RI1  is currently suppressing the leaky bit, identifying the row associated with the selected wordline WL&lt;K&gt; as including the leaky memory cell. The row address of the leaky cell is then stored (step  345 ) for later consideration. Where redundant rows are included, the row address of leaky cell  270 A can be used to substitute the associated defective row with a redundant row (step  350 ). 
     FIG. 4 depicts a memory assembly  400  with row substitution capability in accordance with one embodiment of the invention. Memory assembly  400  includes memory circuit  200  of FIG. 2 in communication with an in-system configuration (ISC) memory access circuit  410  and a row substitution circuit  450 . Memory circuit  200  receives read voltage V R , first read-inhibit voltage V RI1 , second read-inhibit voltage V RI2 , and control signals via a control bus CTL 0 . Control bus CTL 0  conveys all signals required by wordline select circuit  250  for proper operation. ISC memory access circuit  410  supports a conventional JTAG protocol that allows configuration of devices mounted on a printed-circuit board. ISC memory access circuit  410  includes an address register  415  connected to a data shift register  420 . Address register  415  receives-serial data on a serial input terminal T DI  and serially transmits the data to data shift register  420 . Also, address register  415  can transmit parallel address data to row substitution circuit  440 . Data shift register  420  includes the same number of bits as the columns of memory block  220 . Each bit of data-shift register  420  connects to a corresponding one of the plurality of bitlines. Thus, data shift register  420  either receives serial data from address register  415  or parallel data from bitlines BL&lt;1:M&gt;, and either transmits serial data on output serial terminal TDO or parallel data to bitlines BL&lt;1:M&gt;. 
     Row substitution circuit  450  includes a redundant row  430 , similar to rows  260  of FIG. 2, and a row substitution control circuit  440 . Redundant row  430  includes M memory cells, each connected to a swap wordline SWL and a corresponding one of bitlines BL&lt;1:M&gt;. Row substitution control circuit  440  receives and stores the address of a defective row, as discussed with respect to flowchart  300  of FIG. 3, and controls access to redundant row  430  through swap wordline SWL. For each memory access (read or write), row substitution circuit  440 ,compares the stored address to the contents of address register  415 . If a match is found, indicating address register  415  contains an address for a row identified as defective, row substitution circuit  440  directs the memory access to redundant row  430  and generates a disable signal in response to this address, which disables access to all rows but the redundant-row. Memory assembly  400  thus facilitates row substitution to correct for defective memory cells. 
     FIG. 5 is a block diagram  500  of wordline select circuit  250  (FIGS. 2 and 4) in accordance with one embodiment. Wordline select circuit  250  includes a top decoder  520  receiving and transmitting signals to a row decoder  540 . Wordline voltages V R , V RI1 , and V RI2  are provided to wordline select circuit  250  on like-named terminals. The remaining terminals are part of control bus CTL 0  of FIG.  4 . Top decoder  520  receives control signals A 1 , A 2 , and enable-select signal ENS and transmits input voltage VPNF to row decoder  540  via a selected one of wordline-select lines SELW&lt;1:4&gt;, and input voltage VNNCG via the unselected ones of wordline-select lines SELW&lt;1:4&gt;. Table 1 describes the logical functionality of top decoder  520 . 
     
       
         
               
               
               
               
               
               
               
             
           
               
                 TABLE 1 
               
               
                   
               
               
                 ENS 
                 A1 
                 A2 
                 SELW&lt;1&gt; 
                 SELW&lt;2&gt; 
                 SELW&lt;3&gt; 
                 SELW&lt;4&gt; 
               
               
                   
               
             
             
               
                 0 
                 0 
                 0 
                 VPNF 
                 VNNCG 
                 VNNCG 
                 VNNCG 
               
               
                 0 
                 0 
                 1 
                 VNNCG 
                 VPNF 
                 VNNCG 
                 VNNCG 
               
               
                 0 
                 1 
                 0 
                 VNNCG 
                 VNNCG 
                 VPNF 
                 VNNCG 
               
               
                 0 
                 1 
                 1 
                 VNNCG 
                 VNNCG 
                 VNNCG 
                 VPNF 
               
               
                 1 
                 X 
                 X 
                 VPNF 
                 VPNF 
                 VPNF 
                 VPNF 
               
               
                   
               
             
          
         
       
     
     In a normal read operation, row decoder  540  applies a read voltage VR to a selected wordline and a conventional read-inhibit voltage to the unselected wordlines. In a test-row read operation, row decoder  540  applies read voltage VR to test wordline TWLT, read-inhibit voltage VRI 1  to one of wordlines WL&lt;1:N&gt;, and read-inhibit voltage VRI 2  to the remaining wordlines. Select signals on lines SELB&lt;1:M&gt; and ELW&lt;1:4&gt; determine which wordlines receive which read-inhibit voltage. Decoders  520  and  540  are detailed below. 
     FIG.  6 ( a ) is a block diagram  600  of an embodiment of top decoder  520  of FIG.  5 . Top decoder  520  includes wordline-select circuit  610  receiving control signals A 1 , A 2 , and enable-select ENS and transmitting enable-select-wordline signals ENSW&lt;1:4&gt; to respective select-wordline drivers  620 . Enable-select-wordline signals ENSW&lt;1:4&gt; control whether select-wordline driver  620  transmits input voltage VPNF or input voltage VNNCG to a wordline-select terminal. Thus during operation, wordline-select circuit  610  enables only one of select-wordline drivers  620  to transmit input voltage VPNF on respective wordline-select terminal SELW&lt;1:4&gt; as shown above in Table 1. 
     FIG.  6 ( b ) details an embodiment of select-wordline driver  620  of FIG.  6 ( a ). Select-wordline driver  620  includes a voltage-level shifter  660  that shifts enable-select-wordline signal ENSW from switching between a voltage range of zero-to-VDD to a voltage range of zero-to-VPNF. Voltage-level shifter  660  then applies the level-shifted signal to a second voltage-level shifter  670 . 
     Voltage-level shifter  670  shifts the level shifted signal from a voltage range of zero-to-VPNF to a voltage range of VNNCG-to-VPNF. Voltage-level shifter  670  transmits the resulting voltage-level shifted signal to an output circuit  680 . Output circuit  680  then generates a select-wordline signal SELW, a version of enable-select wordline signal ENSW, exhibiting a broader voltage range. In one embodiment, input voltages VPNF and VNNCG are three and negative four volts, respectively. Select-wordline circuit  620  thus level-shifts enable-select wordline signals ENSW, switching between supply voltage and ground, to output signal (enable-select wordline ENWL), switching between three and negative four volts. 
     FIG.  7 ( a ) details row decoder  540  of FIG. 5 in accordance with one embodiment of the invention. As noted above, row decoder  540  applies read-inhibit voltage V RI1  to one of wordlines WL&lt;1:N&gt; and applies read-inhibit voltage V RI2  to the remaining wordlines. 
     Row decoder  540  includes a plurality of row driver blocks  710  and a test row driver block  720 . Each row driver block  710  connects to select-wordline signals SELW&lt;1:4&gt; and one of M select-block signals SELB&lt;1:M&gt;. The appropriate select-block signals SELB&lt;i&gt; (a block index).and select-wordline signals SELW&lt;1:4&gt; are asserted to apply the first read-inhibit voltage V RI1  to a selected wordline; the remaining wordlines receive the second read-inhibit voltage V RI2 . To apply the first read-inhibit voltage on wordline WL&lt;3&gt;, for example, select-block signal SELB&lt;1&gt; and select-wordline signal SELW&lt;3&gt; are asserted. 
     Test row driver block  720  is similar to row driver blocks  710 , but is modified such that it is active only during test-row read operations. During a test-row read operation, test-select-wordline signal SELt is asserted and read voltage V R  applied to terminal V RI1 . In response, test row driver block  720  transmits read voltage V R  to test wordline WLT. 
     FIG.  7 ( b ) details an embodiment of row driver  710  of FIG.  7 ( a ). Row driver  710  includes an enable-wordline driver circuit  765  similar to select-wordline driver  620  of FIG.  6 ( a ) receiving input voltages,. VPNF and VNNCG, and a select-block signal SELB; and transmitting an enable-wordline driver signal ENWLD to wordline drivers  770 . Similar to select-wordline driver  620 , enable-wordline driver  765  shifts seiect-block signal SELB&lt;i&gt; from switching between a voltage range of zero-to-VDD to an enable-wordline driver signal ENWLD switching between a voltage range of VNNCG-to-VPNF. Enable-wordline driver  765  then transmits enable-wordline driver signal ENWLD to wordline drivers  770 . Table 2 summarizes logic functionality of enable-wordline circuit  765 . 
     
       
         
               
               
             
           
               
                 TABLE 2 
               
               
                   
               
               
                 SELB&lt;i&gt; 
                 ENWLD 
               
               
                   
               
             
             
               
                 0 
                 VNNCG 
               
               
                 1 
                 VPNF 
               
               
                   
               
             
          
         
       
     
     Wordline drivers  770  receive an enable-wordline driver signal ENWLD and a respective one of select-wordline signals SELW&lt;1:4&gt;, and either transmits a first read-inhibit voltage VRI 1  or a second read-inhibit voltage VRI 2  on wordline terminal WL. Table 3 summarizes the functionality of wordline drivers  7706 . 
     
       
         
               
               
               
               
               
               
               
               
               
             
           
               
                 TABLE 3 
               
               
                   
               
               
                 ENWLD 
                 SELW0 
                 SELW1 
                 SELW2 
                 SELW3 
                 WL&lt;0&gt; 
                 WL&lt;1&gt; 
                 WL&lt;2&gt; 
                 WL&lt;3&gt; 
               
               
                   
               
             
             
               
                 VPNF 
                 VPNF 
                 VNNCG 
                 VNNCG 
                 VNNCG 
                 VRI1 
                 VRI2 
                 VRI2 
                 VRI2 
               
               
                 VPNF 
                 VNNCG 
                 VPNF 
                 VNNCG 
                 VNNCG 
                 VRI2 
                 VRI1 
                 VRI2 
                 VRI2 
               
               
                 VPNF 
                 VNNCG 
                 VNNCG 
                 VPNF 
                 VNNCG 
                 VRI2 
                 VRI2 
                 VRI1 
                 VRI2 
               
               
                 VPNF 
                 VNNCG 
                 VNNCG 
                 VNNCG 
                 VPNF 
                 VRI2 
                 VRI2 
                 VRI2 
                 VRI1 
               
               
                 VNNCG 
                 X 
                 X 
                 X 
                 X 
                 VRI2 
                 VRI2 
                 VRI2 
                 VRI2 
               
               
                   
               
             
          
         
       
     
     From table 3 it can be seen that only the selected wordline transmits first read-inhibit voltage V RI1  while all unselected wordlines transmit second read-inhibit voltage V RI2  Thus during each test row read operation, only one wordline, the selected wordline, transmits head inhibit voltage V RI1 . 
     FIG.  7 ( c ) details an embodiment of row driver circuit diagram  770  of FIG.  7 ( b ). Wordline driver  770  includes conventional NAND and inverter gate configurations  780  and  785 , respectively, having VPNF and VNNCG as supply voltages. NAND configuration  780  applies output signal EN to inverter configuration  785  and to a first control terminal of multiplexer  790 . Inverter configuration  785  applies output signal ENb to a second control terminal of multiplexer  790 . Multiplexer  790  transmits either first read-inhibit voltage V RI1  or second read-inhibit voltage VRI 2  to wordline output terminal WL as directed by control signals EN and ENb. 
     FIG.  7 ( d ) details an embodiment of multiplexer  790  of FIG.  7 ( c ). Multiplexer  790  includes first and second CMOS full pass gates  796  and  798  that alternately pass first read-inhibit voltage V RI1  or second read-inhibit voltage V RI2  as directed by enable signals EN and ENb. 
     While the present invention has been described in connection with specific embodiments, variations of these embodiments will be obvious to those of ordinary skill in the art. For example, instead of applying the second read-inhibit voltage to selected wordline and the first read-inhibit voltage to unselected wordlines, the first read-inhibit voltage can be applied to selected wordline and the second read-inhibit voltage to unselected wordlines. Moreover, some components are shown directly connected to one another while others are shown connected via intermediate components. In each instance the method of interconnection establishes some desired electrical communication between two or more circuit nodes, or terminals. Such communication may often be accomplished using a number of circuit configurations, as will be understood by those of skill in the art. Therefore, the spirit and scope of the appended claims should not be limited to the foregoing description.