Abstract:
An apparatus including a phase detector to detect a phase difference between an output clock signal and a local reference clock signal comprising a first sampling circuit and a second sampling circuit to cross-sample the output clock signal and the local reference clock signal respectively and a comparator circuit coupled to the two sampling circuits that detects the phase difference.

Description:
FIELD OF THE INVENTION 
     The invention relates to delay locked loop based circuits for adaptive clock generation. 
     BACKGROUND 
     As the level of integration in semiconductor integrated circuits (ICs) increases, signal delays due to parasitic resistance-capacitance loading become larger. This is especially true of high fan-out global signal lines such as synchronous clocks. Clock signals in modern programmable logic devices may drive several thousand registers. This is a considerable load to the clock driver. Clock tree structures can be implemented on chip to minimize clock skew among registers. However, the base trunk clock driver must be capable of driving this clock tree structure and, as a result, a buffer delay of several nanoseconds is typically incurred. 
     Circuits using phase locked loop (PLL) are widely used in data communications. An example of such a circuit may be a de-skew clock generation circuit. A typical PLL consists of three on-chip functions and a loop filter. A phase detector measures the phase and frequency difference between an external reference signal and an internal timing signal. Based on the sign and magnitude of the difference, the phase detector drives a charge pump that raises or lowers the voltage level of the loop filter. The loop filter provides a stable voltage input to a voltage controlled oscillator (VCO). The VCO develops a timing signal that is fed back to the phase detector for comparison with the incoming reference signal. When the reference signal and the VCO timing signal are identical the PLL is “locked” onto the reference signal. 
     A PLL based circuit may be generally sufficient where power dissipation is not an issue even though communication speeds are high. In certain circuits, communication speeds may range from Megahertz (MHz) to Gigahertz (GHz). In general, however, circuits operating at high speeds are sensitive to power dissipation that results in overheating of the circuits. In circuits where power conservation is an issue, power dissipation is also problematic. As well, problems exist with implementing a PLL in a typical integrated circuit since the PLL uses analog devices such as a phase frequency detector (PFD), charge pump and low pass filter. These problems include, among others, poor stability and performance in a noisy environment. 
     SUMMARY 
     In accordance with an embodiment of the invention, there is disclosed an apparatus including a phase detector to detect a phase difference between an output clock signal and a local reference clock signal comprising a first sampling circuit and a second sampling circuit to cross-sample the output clock signal and the local reference clock signal respectively and a comparator circuit coupled to the two sampling circuits that detects the phase difference. A digitally controlled delay line is coupled to the output clock signal to adaptively adjust a delay to compensate for the phase difference. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     The accompanying drawings are included to provide a further understanding of the invention, and are incorporated in and constitute a part of this specification. The drawings illustrate embodiments of the invention and, together with the description, serve to explain the principles of the invention. In the drawings, 
     FIG. 1 is a block diagram of a Delay Locked Loop (DLL) based de-skew clock generation circuit in accordance with an embodiment of the invention; 
     FIG. 2 illustrates an output clock that is either aligned or has a constant controllable shift with the input clock in accordance with an embodiment of the invention; 
     FIG. 3 is a schematic diagram of a phase detector circuit in accordance with an embodiment of the invention; 
     FIG. 4 is a schematic diagram of a fine digital delay line (FDDL) in accordance with an embodiment of the invention; 
     FIG. 5 illustrates a typical single-stage differential circuit structure, including a current bias, an input component pair, and a load component pair in accordance with an embodiment of the invention; 
     FIG. 6 illustrates a symmetric differential complimentary metal-oxide semiconductor (SDCMOS) structure with improved circuit reusability in accordance with an embodiment of the invention; 
     FIG. 7 illustrates a high speed CMOS differential buffer for either input, intermediate, or output stages in accordance with an embodiment of the invention; 
     FIG. 8 is a schematic diagram of a coarse digital delay line (CDDL) in accordance with an embodiment of the invention; 
     FIG. 9 is a schematic diagram of a coarse delay buffer bit which forms part of the CDDL in accordance with an embodiment of the invention; 
     FIG. 10 is a schematic diagram of a differential multiplexer which forms part of the CDDL in accordance with an embodiment of the invention; 
     FIG. 11 is a schematic diagram of a differential output buffer structure which forms part of the de-skew clock generation circuit in accordance with an embodiment of the invention; 
     FIG. 12 is a schematic diagram of a system wherein a peripheral controller comprises a de-skew clock generation circuit and is coupled to a processor that is adapted to access data from the peripheral controller in accordance with an embodiment of the invention. 
    
    
     DETAILED DESCRIPTION 
     When used in a de-skew clock generation circuit, in one embodiment, the de-skew clock generation circuit uses a controlled digital delay line to adjust the delay through a pre-defined z-domain algorithm to compensate for the phase error. As a result, the output clock will be phase-locked to the input (reference) clock independent of the loading condition. In this manner, a DLL-based de-skew clock generation circuit achieves very short acquisition time when compared to the acquisition time of the PLL. Furthermore, the de-skew clock generation circuit is highly jitter tolerant. Thus, from above, it can be seen that these features make the DLL de-skew clock generation circuit particularly suitable for various low power and high-speed applications. 
     The operation of a delay locked loop (DLL) may use a voltage controlled delay line (VCDL) rather than a VCO to generate the output timing signal. DLLs lock onto reference signals faster than PLLs and they produce output signals with less jitter. Multiple chips on a printed circuit board or cores of different sizes within a single system on a chip can experience clock skew. By using DLL technology to shift the phase of the reference clock within each chip or core, designers can minimize skew and tune a system to perform up to its potential. DLL devices can be used in each chip or core to compensate not only for loading differences but also for delays that arise with process, voltage, and temperature (PVT) differences. 
     The scheme may be implemented, in one aspect, using a digital-based analog (DBA) design approach, which utilizes analog functions using digital circuits based on certain digital signal processing (DSP) algorithms. The DBA approach makes the circuit implementation highly scalable and allows the circuit to be directly integrated onto a digital-based chip without degrading its reliability, manufacturability and testability. Various embodiments will be described to aid in the understanding of the invention and should not be construed as limitations of the invention. 
     FIG. 1 is a block diagram of a Delay Locked Loop (DLL) based de-skew clock generation circuit in accordance with an embodiment of the invention. As shown in the figure, de-skew clock generation circuit  5  comprises digitally controlled delay line (DCDL)  10 , phase detector  15 , and output clock buffer  20 . To aid in the understanding of the invention, an overview of the embodiment is given below. 
     As shown, in FIG. 2, one purpose of de-skew clock generation circuit  5  is to adaptively adjust the delay so that output clock  22  will be aligned with input clock  21 . 
     In the implemented phase detector  25  shown in FIG. 3, input reference clock  21  and output clock  22  rising edges are used to generate two narrow pulses  30  and  35  in order to create a delay. Pulses  30  and  35  are used to control cross sampling of the other (the output and the reference clock) signal. NAND gates  40  and  45  are used as pulse generators for cross-sampling the two signals. That is, inverted input clock and the input clock are sent into NAND gate  40  so that a pulse will be generated for cross-sampling. As well, inverted output clock and output clock  22  are sent into NAND gate  45  so that a pulse will be generated for cross-sampling. As a result, the input clock and the output clock will cross-sample each other when switches  50  and  55  are on. This method is also called differential sampling which is used, in one aspect, in order to achieve more accuracy. 
     The sampled signals are then compared using comparator  60  to provide the phase difference of clocks  21  and  22  and to issue the delay line control signals. Comparator  60  will determine if output clock signal  22  is lagging or leading input reference signal  21 . At a particular sampling point, if input clock  21  is high and output clock  22  is low, then comparator  60  will detect that output clock signal  22  is lagging input clock  21 . If input clock  21  is low and output clock  22  is high then comparator  60  will detect that output clock signal  22  is leading the input. This method of differential sampling eliminates the condition where both signals are high or both are low, thus increasing accuracy of the circuit. The information obtained from comparator  60  will then be relayed to fine digital delay line (FDDL)  70  as shown in FIG. 4 and, where necessary, course digital delay line (CDDL)  85 . 
     Digitally controlled delay line (DCDL)  10  unit consists of two sub-blocks  70  and  85  as shown in FIGS. 4 and 8, respectively, for either fine or coarse delay compensations. Fine digital delay line (FDDL)  70  uses a plurality of digital controllable differential delay buffer cells  75 . 
     In recent years, there have been significant efforts in the development of mixed-signal circuits, primarily driven by the benefits of cost reduction and performance enhancement through analog and digital circuit integration onto a single chip. Differential circuits, which generally have better signal integrity with larger noise margin and lower noise generation, are widely used in analog and signal-integrity-critical digital circuit implementations of the mixed signal chips. Shown in FIG. 5 is a single-stage differential circuit structure, consisting of a current bias, an input component pair, and a load component pair. However, these type of circuits generally require very careful selection of all devices and circuit parameters (sizing, biasing, signal swings, gain, speed, drive capability, etc). Still further, significant tuning or even re-design are usually required for different applications or using different manufacture process technologies due to the highly process dependent nature of the device parameters. Consequently, development of highly reusable differential analog and digital circuits will be very important for the success of the future low cost mixed signal VLSI chips. 
     In one embodiment of the invention, each buffer cell  75  includes a symmetric differential complimentary metal-oxide semiconductor (SDCMOS) structure. As shown in FIG. 6, in one embodiment, the basic SDCMOS circuit uses two CMOS transistor pairs (M 1 , M 2 , M 3 , M 4 ) as the input devices, which extend the input signal to full swing. Additional two CMOS transistor pairs (M 5 , M 6 , M 7 , M 8 ) are used for either current biases or loads. The gates of the bias/load branches are shorted together at points “p” and “n”. As can be seen, the entire circuit is symmetric at both left-to-right and top-to-bottom directions. There are three feedback loops in this circuit structure, including the left loop by transistor M 1 , M 2 , M 5 , and M 6 , the right loop by transistor M 3 , M 4 , M 7 , and M 8  and a common mode loop by all transistors as represented by “p” and “n” in FIG.  6 . For example, a signal at V in  will generate a current I 1  through transistor M 6 . Likewise, a signal at V in  # will generate a  12  through transistor M 8 . Both currents will join at common mode “p” to form current I c , where I c =I 1 +I 2 . In the same manner, a signal at V in  will also generate a current I 3  through transistor M 5 , and a signal at V in  # will generate a current I 4  through transistor M 7 . Both currents will join at common mode “n” to form current I c , where I c =I 3 +I 4 . The circuit configuration illustrated is dynamically self-biased. It can provide higher bias current around the cross-point to achieve zero dc-bias, high speed, and a “soft landing” (avoiding noise and glitches in the signal). These properties generally make SDCMOS circuits very robust on various applications situations (large power supply range, rail-to-rail signal swings, large transistor size range, etc., and very scalable on different manufacture process technologies. 
     The SDCMOS structure illustrated in FIG. 6 can be used for various mixed-signal applications. Shown in FIG. 7 is a high speed CMOS differential buffer for either input, intermediate, or output stages. Two leakage transistors Mp and Mn are used in this circuit to eliminate the dc-path in the down stream circuit by pulling up or down the outputs to rail during the power down mode. In one chip structure, simulation shows that this dc-path elimination technique significantly reduces the static current of the circuit. For a large size down-stream circuit of the same type, such as the interconnect driver/repeater of the clock or critical signals used in one application, this technique can provide significant power reduction. 
     The total delay that can be adjusted in FDDL  70  can be represented by N (t 2 −t 1 ) where N is the number of buffer cells in FDDL  70 , “t 2 ” is the total delay needed, and “t 1 ” is the intrinsic delay due to gates. Time constant (t 2 ) can be represented by R (C 1 +C 2 ) where R is the effective resistance, C 1  is the parasitic capacitance, and C 2  is the capacitance controlled by the switch or transistor. Therefore, every time a “1” is input into shift register  80 , a fixed delay of “t 2 ” is generated from the buffer cell in FIG.  6 . As well, if a “0” is input into shift register array  80 , an intrinsic delay of “t 1 ” is generated from the buffer cell in FIG.  6 . For example, where N=6 stages in FDDL and the register contains 1 1 0 0 0 0, then the total delay will be 6 t 1 +2(t 2 −t 1 ). 
     The delay of each cell in DCDL  10  can only be one of two discrete values separated by about 80 pico seconds (ps), controlling through a digital input. The entire FDDL  70  is controlled through a multi-bit bi-directional shift register array, where a 12-bit register is one embodiment because  12  bits will cover at least a one step delay in CDDL  85 . An overflow “O” as represented in FIG. 4 will occur when the shift register array is filled with “1”s, and another shift-right operation is needed to increase delay. Likewise, an underflow “U” as represented in FIG. 4 will occur when the shift register array is filled with “0”s, and another shift-left operation is needed to decrease delay. 
     The number of “0”&#39;s or “1”&#39;s stored inside the register array can be linearly controlled through the left or right shift operation of the shift registers according to the sign of the phase difference from phase detector  25 . For example, if phase detector  25  detects a lag by the sampled output clock, then the delay of the output clock must be decreased, which will be satisfied using a shift left operation. If phase detector  25  detects a lead by the sampled output clock, then the delay of the output clock must be increased, which will be satisfied using a shift right operation. 
     The coarse delay compensation can be accomplished by CDDL  85  unit as shown in FIG. 8, which changes the number of identical delay buffer cells in the clock path using multiplexers  95 . As shown in FIG. 6, multiplexers  95  are controlled by a multi-bit up/down binary counter  100  which, in turn, is controlled by the underflow (U) or overflow (O) flag signals from FDDL  70  in FIG.  4 . An exclusive-OR gate is connected to the enable signal, therefore counter  100  will be enabled whenever an underflow (U) or overflow (O) flag signal is sent from FDDL  70 . In addition, counter  100  will move up or down depending on whether an overflow bit is detected or not. The total delay will be the sum of delays obtained from FDDL  70  and CDDL  85 . 
     For example, if counter  100  displays 1 0 0 0 0, then a delay of 16 total delay (t d ) will be generated by coarse delay buffer bits as shown in FIG. 9, where each bit will yield a fixed delay td since, in this embodiment, there is no switching circuitry. 
     The differential multiplexer (MUX), as shown in FIG. 10, will select a delay according to the corresponding bit in up/down counter  100 . For example, using the previous example of 1 0 0 0 0, where the bit is “0”, the MUX will choose the path where only an intrinsic delay is obtained. And, where the bit is “1”, the MUX will choose the path where a delay of 16 t d  is obtained. 
     Output buffer  20  is used to improve the loading capability of the delay-locked loop circuit. In this embodiment, output buffer  20  consists of four increasingly sized differential buffer stages of similar structure as shown in FIG.  11 . With output buffer  20 , a smaller DCDL  10  can be used. In the de-skew clock application, the feedback clock is usually tapped at the input of the load after output buffer  20 . However, early or late output clocks can also be obtained by purposely adding a known delay value in the reference or feedback clock path. 
     FIG. 12 is a schematic diagram that illustrates a system  105  wherein a peripheral controller  125  comprises a de-skew clock generation circuit  130  similar to the de-skew clock generation circuit described above. FIG. 12 illustrates but one application of the invention, that is the personal computer, but may be replaced by other applications such as a workstation, server, Internet driver or other fabric channels used as a link. In FIG. 12, peripheral controller  125  is coupled to processor  115  via a serial or parallel bus  120 . Processor  115  is adapted to access data from peripheral controller  125  via bus  120 . Memory  110 , and display controller  135 , may also be coupled to peripheral controller  125  via bus  120 . Monitor  140  may also be coupled to display controller  135 . Other peripheral devices  145 , such as a mouse, CD-ROM and video, may also be coupled to peripheral controller  125 . 
     Some design advances of the circuit described in this invention include: a) high scalability, the feedback control mechanism being based on the pre-designed digital filter algorithm, not the process technology, b) high noise immunity where all critical components are designed using differential circuit technique, c) high reusability and short design time, the design being very modular and regular, d) smaller area and low power, thus there is no explicit capacitor or resistor in the design and most devices in the design are close to minimum. This technology can be used for various de-skew clock generation for either on-chip or off-chip circuits. 
     In the preceding detailed description, the invention is described with reference to specific embodiments thereof. It will, however, be evident that various modifications and changes may be made thereto without departing from the broader spirit and scope of the invention as set forth in the claims. The specification and drawings are, accordingly, to be regarded in an illustrative rather than a restrictive sense.