Abstract:
A high efficiency dual-band RF power amplifier has an output and/or input of a high frequency transistor well terminated at the second harmonic frequency for dual-band operation. Diode switches or voltage controlled varactors implement dual-band resonators such that they can offer low impedance at the second harmonic of each frequency band, while, in some cases, presenting high impedance at the fundamental frequency as an RF choke circuit.

Description:
BACKGROUND OF THE INVENTION 
     1. Field of the Invention 
     The present invention relates to dual-band RF (Radio Frequency) power amplifiers. More particularly, this invention relates to high efficiency RF power amplifiers having a switching circuit, which creates a low impedance at the second harmonic of each frequency band, for dual-band operation. 
     2. Description of the Related Art 
     In portable wireless communication systems, there is a strong need for power amplifiers with high efficiency to maximize the amount of talk time obtained from a power source, such as a battery. It is well known in the art of RF power amplifiers to consider both the fundamental frequency, and harmonic components of the fundamental frequency, for increasing the efficiency to an optimal level. In addition to obtaining impedance matching at the fundamental frequency, the efficiency is increased by conditions that provide zero impedance for even multiples (even harmonics) of the fundamental frequency. The following background documents are incorporated by reference herein in their entireties: 
     [1] D. M. Snider,” A Theoretical Analysis and Experimental Confirmation of the Optimally Loaded and Overdriven RF Power Amplifier,”  IEEE Tran, Electron Devices,  vol. ED-14, pp. 851-857, December 1967. 
     [2] J. E. Mitzlaff, “High Efficiency RF Power Amplifier,” U.S. Pat. No. 4,717,884, January 1988. 
     [3] M. A. Khatibzadeh, “Monolithically Realizable Harmonic Trapping Circuit,” U.S. Pat. No. 5,095,285, March 1992. 
     [4] N. Furutani, et al., “High Efficiency RF Power Amplifier,” U.S. Pat. No. 5,159,287, October 1992. 
     [5] P. M. White, “Effect of Input Harmonic Terminations of High Efficiency Class-B and Class-F Operation of PHEMT Devices,”  IEEE MIT - S Dig ., pp. 1611-1614, 1998. 
     [6] M. Masahiro, et al., “Radio-Frequency Power Amplifier with Input Impedance Matching Circuit Based on Harmonic Wave,” U.S. Pat. No. 5,592,122, January 1997. 
     [7] A. Adar, “Multiple-Band Amplifier,” U.S. Pat. No. 5,774,017, June 1998. 
     A Class F amplifier is well known as a device which operates primarily as a switch. For this reason, the power dissipation is lower and the stage efficiency is higher than for other amplifiers. Class F operation is characterized by limiting the voltage across the active device to approximately twice the supply voltage [reference 2]. Class F power amplifiers are a most popular design because they are known for high efficiency, wherein the impedance at even harmonic frequencies at the transistor output (drain or collector) is set to a short-circuit (low impedance), and the impedance at the odd harmonic frequencies at the transistor output is set to an open-circuit (high 8 infinite impedance) [references 1-4]. The derivation of the harmonic impedance of a Class F amplifier [reference 1] is based on a Class B biasing operation. In Class B operation, the current flows for only 180° of the AC cycle, whereas in Class A operation, the transistor is active for 360° of the AC cycle for a linear reproduction of the input. When the amplifier is biased at a Class AB state (which is a hybrid between Class A and Class B operation, i.e. the bias voltage is chosen so that current flows for more than half of the cycle for higher efficiency than Class A but does not provide a linear reproduction like Class A), the impedance of the even harmonics is still zero, but the impedance of the odd harmonics is no longer infinite. 
     In addition, it is well known that second harmonic frequency termination is a dominant factor in improving the efficiency of a power amplifier. Furthermore, providing the second harmonic termination at the transistor input (gate or base), in addition to the transistor output, may improve the overall efficiency significantly [references 5, 6]. 
     FIG. 1 shows a circuit diagram of a conventional single band high efficiency power amplifier. The even harmonic resonator  1  provides zero impedance for the second harmonic, and the input and output fundamental matching network  2 , 3  provides the prescribed load impedance at the fundamental frequency to Field Effect Transistor (FET)  4 . However, dual-band operation in portable units is becoming indispensable because of dual-band communication systems, such as GSM (Global System for Mobil Communications). 
     However, the conventional high efficiency power amplifier shown in FIG. 1 can not provide dual-band operation. Although two single band power amplifiers, each of which operate at a specific frequency band, can be used in a dual-band handset (e.g., a telephone), a single dual-band amplifier provides instant reductions in the costs of manufacture and allows for a reduction in the size of the respective device, and saves power. 
     In addition, in the dual-band GSM system, the second harmonic of the cellular frequency band (around 900 MHz) is within the fundamental PCS (Personal Communications System) frequency band (around 1800 MHz). These frequency values indicate that a high efficiency GSM dual-band power amplifier should provide a low impedance at around 1800 MHz at the transistor output (or/and input) under cellular-band operation, and provide a prescribed impedance at around 1800 MHz and a low impedance at around 3600 MHz under PCS-band operation. Thus, there is a need for a single amplifier having dual-band capabilities that overcomes the problems of the prior art. 
     SUMMARY OF THE INVENTION 
     Accordingly, it is an object of the present invention to develop a high efficiency RF power amplifier for dual-band application. 
     To this end, according to the present invention, there is provided a high efficiency dual-band RF power amplifier which comprises (1) a power transistor having an input and an output; (2) a dual-band input impedance matching circuit connected to the input of the power transistor for providing input impedance matching for the RF power amplifier at two desired fundamental frequency bands; (3) a dual-band output impedance matching circuit connected to the output of the power transistor for providing output impedance matching for the RF power amplifier at two desired fundamental frequency bands; and (4) a combined dual-band bias circuit and second harmonic frequency termination circuit connected to one or both of the output and the input of the power transistor for providing an RF choke at a fundamental wave frequency and for providing a low impedance at a second harmonic frequency with respect to the fundamental wave frequency of each band. 
     The dual-band bias circuit and harmonic frequency termination circuit can include a band select voltage terminal for receiving a band select voltage. The dual-band input impedance matching circuit can comprise a passive dual-band network. The dual-band input impedance matching circuit can comprise one of a duplexer and a switch for providing impedance matching at two frequency bands of dual-band operation. The dual-band output impedance matching circuit can comprise a passive dual-band network. The dual-band output impedance matching circuit can comprise one of a duplexer and a switch for providing impedance matching at two frequency bands of dual-band operation. 
     The combined dual-band bias circuit and second harmonic frequency termination circuit can comprise (a) a bias circuit comprising: a transmission line and a bypass capacitor; the transmission line having an electric length which is approximately {fraction (1/20)} th  of the fundamental wave frequency; a first end of the transmission line being connected to a first bias terminal and the bypass capacitor; a second end of the transmission line being connected to the output terminal of the power transistor; and (b) a second harmonic frequency termination circuit connected to the bias circuit, the second harmonic frequency termination circuit comprising: a first series resonant circuit comprising a cascaded inductor and capacitor, the first series resonant circuit having a first end connected to the output terminal of the power transistor and a second end connected to ground; a second series resonant circuit comprising a cascaded inductor and capacitor, the second series resonant circuit having a first end connected to the output terminal of the power transistor, a switch having a first end connected to a second end of the second series resonant circuit and a second end connected to ground; a bias resistor connected to the first end of the switch and to a second bias terminal for providing a band select voltage so that the switch receives a band select voltage (Vb) from the second bias terminal via said bias resistor. 
     The switch can be a diode having an anode and a cathode, where the cathode of the diode is connected to ground; and the anode of the diode is connected to the bias resistor for receiving the band select bias voltage (Vb) from the second bias terminal. 
     The combined dual-band bias circuit and second harmonic frequency termination circuit can alternatively comprise: (a) a bias circuit comprising a transmission line and a bypass capacitor; the transmission line having an electric length of approximately a quarter wavelength at a fundamental wave frequency of a lower frequency band; a first end of the transmission line being connected to a first bias terminal and the bypass capacitor; a second end of the transmission line being connected to the output of the power transistor; and (b) a second harmonic frequency termination circuit comprising: a first DC blocking capacitor having a first end connected to the first end of the transmission line; a diode for switching virtually between a lower frequency path and a higher frequency path through the transmission line, said diode having a cathode connected to a second end of the first DC blocking capacitor; a second DC blocking capacitor having one end connected to the anode of the diode and another end coupled to an interior point of the transmission line such that the length between the interior point and the second end of the transmission line is approximately a quarter wavelength at the fundamental wave frequency of a higher frequency band; a bias resistor having a first end connected to the anode of the diode and a second end connected to a second bias terminal for providing band select voltage; and an RF choke inductor having a first end connected to the cathode of the diode and a second end connected to ground to provide a DC return path. 
     The combined dual-band bias circuit and second harmonic frequency termination circuit can further alternatively include: (a) a bias circuit comprising a transmission line and a bypass capacitor; the transmission line having an electric length less than a quarter wavelength of the fundamental frequency; a first end of the transmission line being connected to a first bias terminal and the bypass capacitor; a second end of the transmission line being connected to the output terminal of the power transistor; and (b) a second harmonic frequency termination circuit comprising: a series resonant circuit comprising a capacitor, an inductor and a varactor, which are all cascaded, the series resonant circuit having a first end connected to the output terminal of the power transistor and a second end connected to ground; and an RF choke inductor having one end connected to the varactor and the inductor of the series resonant circuit and another end connected to a second bias terminal for providing a band select voltage. 
     The transmission line can have an electric length less than {fraction (1/20)}th of a wavelength of the fundamental frequency. 
     According to the present invention, there is further provided a high efficiency dual-band RF power amplifier comprising (1) a power transistor having an input and an output; (2) a dual-band input impedance matching circuit connected to the input of the power transistor for providing input impedance matching for the RF power amplifier at two desired fundamental frequency bands; (3) a dual-band output impedance matching circuit connected to an output of the power transistor for providing output impedance matching for the RF power amplifier at two desired fundamental frequency bands; and (4) a dual-band second harmonic frequency termination circuit connected to one of the output and the input of the power transistor for setting a low impedance for a second harmonic frequency with respect to a fundamental wave frequency of each band. 
     The dual-band bias circuit and harmonic frequency termination circuit can include a band select voltage terminal for receiving a band select voltage. The dual-band input impedance matching circuit can comprise a passive dual-band network. The dual-band input impedance matching circuit can comprise one of a duplexer and a switch for providing impedance matching at two frequency bands of dual-band operation. The dual-band output impedance matching circuit can comprise a passive dual-band network. The dual-band output impedance matching circuit can comprise one of a duplexer and a switch for providing impedance matching at two frequency bands of dual-band operation. 
     The dual-band second harmonic frequency termination circuit can comprise (a) a series resonant circuit formed of a cascaded inductor, a capacitor and a varactor, the series resonant circuit having a first end connected to the output terminal of the power transistor and a second end connected to ground; and (b) an RF choke inductor with one end connected to the junction between the inductor and the varactor in the series resonant circuit and another end connected to a first bias terminal. 
     The dual-band second harmonic frequency termination circuit can alternatively comprise (a) a first transmission line and a second transmission line; (b) the first transmission line having an electrical length approximately ⅛ th  of a wavelength at a fundamental wave frequency of a higher frequency band; (c) a DC blocking capacitor having one end connected to the output terminal of the power transistor and another end connected to a first end of the first transmission line; (d) a diode providing a switching function between the first and the second transmission line; the diode having an anode connected to a second end of the first transmission line and to a second bias terminal for providing a band select bias via a bias resistor and the diode having a cathode connected to one end of the second transmission line: and (e) an RF choke inductor connected at a first end to the cathode of the diode and a second end connected to ground; the second transmission line having an electrical length, when added to the length of the first transmission line, equal to approximately ⅛ th  of a wavelength at a fundamental wave frequency of a lower frequency band; and another end of the second transmission line being open. 
     The dual-band second harmonic frequency termination circuit can further alternatively comprise: (a) a series resonant circuit comprising a transmission line having a first end connected to a first end of a capacitor and a second end connected to ground; the transmission line having an electrical length less than a quarter wavelength at a fundamental wave frequency of a lower frequency band; the capacitor having one end connected to the output terminal of the power transistor and another end connected to the first end of the transmission line; (b) a diode for providing virtually a switching function between a lower frequency path and a higher frequency path of the transmission line; the diode having a cathode coupled to an interior point of the transmission line; and (c) a DC blocking capacitor having one end connected to the first end of the transmission line and another end connected to an anode of the diode and to a second bias terminal for providing a band select voltage (Vb) via a bias resistor. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is a circuit diagram showing an exemplary configuration of a conventional high efficiency RF power amplifier. 
     FIGS. 2A and 2B are circuit diagrams respectively showing the configurations of first and second embodiments of dual-band RF high efficiency power amplifiers according to the present invention. 
     FIG. 3 is a circuit diagram showing one embodiment of the terminator and choke circuit of FIG.  2 A. 
     FIG. 4 is a circuit diagram showing another embodiment of the terminator and choke no circuit of FIG.  2 A. 
     FIG. 5 is a circuit diagram showing yet another embodiment of the terminator and choke circuit of FIG.  2 A. 
     FIG. 6 is a circuit diagram showing an embodiment of the terminator circuit of FIG.  2 B. 
     FIG. 7 is a circuit diagram showing another embodiment of the terminator circuit of FIG.  2 B. 
     FIG. 8 is a circuit diagram showing yet another embodiment of the terminator circuit of FIG.  2 B. 
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     FIGS. 2A and 2B show two basic circuit diagrams of the present invention. The high efficiency dual-band power amplifier embodied in FIG. 2A includes a switching dual-band second harmonic termination circuit and RF choke  5   a , whereas the power amplifier embodied in FIG. 2B provides only a dual-band second harmonic termination circuit  5   b . In both embodiments, a control voltage Vb provides a control voltage to determine which band is selected. It should be noted that while the disclosed embodiments exemplify dual-band systems, the implementation of three or more band systems would involve similar structure and operation. 
     The power transistor  6  can be an FET or a BJT (bipolar junction transistor). The dual-band fundamental matching network  7 ,  8  provides a passive dual-band matching network, or a two-path matching network split by a passive duplexer or an active switch. The dual-band harmonic termination circuits  5   a,    5   b  can be implemented by various resonators including a switch or a varactor by which an external control voltage can select different operation bands. For high efficiency, the dual-band harmonic termination circuits may be arranged at either the transistor output or input or both, depending on the specific design. According to the present invention, some of the dual-band harmonic termination circuits can only provide a low impedance at the second harmonic (FIG.  2 B), while others (FIG. 2A) can additionally provide a high impedance at the fundamental wave. This high impedance at the fundamental wave allows the dual-band harmonic termination circuit to be utilized as an RF choke in the bias circuit, as shown in FIG.  2 A. 
     The first embodiment of the present invention includes a fundamental frequency RF choke and a second harmonic frequency termination circuit  5   a  for dual-band operation, whereas the second embodiment only provides a dual-band second harmonic frequency termination circuit  5   b.    
     FIGS. 3 to  5  represent variations of the first embodiment of the present invention shown in FIG. 2A, while FIGS. 6 to  8  represent variations of the second embodiment of the present invention shown in FIG.  2 B. 
     FIG. 3 is a circuit diagram showing a dual-band RF power amplifier in accordance with one variation of the first embodiment of the present invention. The power amplifier includes an FET  6 , a dual-band input impedance matching circuit  7  connected to an input side of the FET  6 , and a dual-band output impedance matching circuit  8  connected to an output side of the FET  6 . 
     Circuit  5   a  functions as a biasing circuit and a second harmonic frequency termination circuit. The biasing circuit comprises a transmission line  9  coupled to a bypass capacitor  10 , and the second harmonic termination circuit comprises inductors  11 ,  12 , capacitors  13 ,  14 , and a switch  15  for dual-band operation. The switch circuit  15  can be realized by a pin diode (as shown in the figure) or any other type of switching device. The cathode of the diode  15  is connected to ground, and a bias resistor  16  is disposed between the anode of the diode  15  and the band-select voltage Vb. An RF choke can be substituted for resistor  16 . 
     For the lower frequency band, the pin diode  15  conducts when the band select bias voltage Vb is applied to the anode of the diode  15  through the bias resistor  16 . The inductor  12 , capacitor  14 , and the conducting diode  15  form a series resonator to provide a low impedance at the second harmonic of the lower frequency band f L . Additionally, a high impedance at the fundamental frequency is obtained at the drain terminal due to a parallel resonator formed by the transmission line  9 , capacitors  10 ,  13 , and  14 , inductors  11  and  12 , and the conducting diode  15 , without affecting the load impedance determined by the output matching network  8 . When the band-select voltage Vb is removed or zero, the diode  15  is in its off state, which effectively disconnects the series resonator  12 ,  14  from the FET  6 . 
     Accordingly, for a higher frequency band f H , the series resonator comprising inductor  11  and the capacitor  13  provides a low impedance at the second harmonic wave 2f H . Similarly, the transmission line  9 , capacitors  10 ,  13 , and inductor  11  form a high impedance at the drain terminal and serve as an RF choke in the bias circuit. In practice, the inductors  11  and  12  can be implemented in a lumped form, or distributed strip line form. The length of the transmission line  9  is determined by the values of the elements  11 , 12 , 13  and  14 , normally about {fraction (1/20)} th  wavelength of the lower fundamental frequency f L . 
     FIG. 4 is a circuit diagram depicting a variation of the first embodiment of the present invention. The interior point of the transmission line  17  is connected to the drain (or collector) bias terminal with a pin diode  18  therebetween. The operating band of the dual-band power amplifier is determined by whether the diode  18  is on or off. The diode is controlled by the band-select voltage Vb which is applied through a bias resistor  19  to the diode  18 , and the inductor  20  provides a DC return path. The resistor  19  may be replaced by an RF choke. The capacitors  21  and  22  are used for DC de-coupling. When Vb is removed or zero, the diode is in its off state, which approximately simplifies the circuit  5   a  to the transmission line  17  and the bypass capacitor  23 . If the length of the transmission line is designed to be approximately {fraction (1/14)} th  wavelength of the lower frequency band f L , then circuit  5   a  provides a high impedance at the fundamental frequency f L , and a low impedance at the second harmonic frequency 2 f L . On the other hand, when Vb is applied to the diode  18 , the diode is in an active state, which effectively modifies the circuit  5   a  into a transmission line with a length of about l h  and a bypass capacitor  23 . If the length of the transmission line l h  is designed to be approximately ¼ th  wavelength of the higher frequency band f H , then circuit  5   a  provides a high impedance at the fundamental frequency f H  and provides a low impedance at the second harmonic frequency 2f H  for the higher operating band. It should be noted that the actual length of l h  also depends on the capacitors  21  and  22  and the pin diode  18 . In addition, a further inductor may be added between capacitors  21 ,  22  and the diode  18  to reduce the required capacitance of each capacitor. 
     FIG. 5 is a circuit diagram of a another variation of the first embodiment of the present invention. The circuit  5   a  functions similarly to the circuit  5   a  in FIG. 3, except that a voltage-controlled varactor  24  replaces the pin diode  15 . The capacitors  24 ,  25  and the inductor  26  form a series resonator to provide a low impedance at the second harmonic wave, and they also form a parallel resonator with the transmission line  9  and the bypass capacitor  10  to provide a high impedance at the fundamental wave. The inductor  26  can be implemented in a lumped form or distributed strip line form. The different band-select voltage Vb, which is provided through inductor  27 , produces different capacitance in the varactor  24 . Therefore, setting appropriate values of Vb enables the circuit  5   a  to function properly at different operating frequency bands. The higher the operating frequency, the lower is the value of capacitance of varactor  24 . In other words, the high efficiency power amplifier in FIG. 5 can also work for multi-band applications. 
     FIG. 6 is a circuit diagram of a second embodiment of the present invention. The drain terminal of the transistor is biased via an RF inductor choke  28  and a bypass capacitor  10 . The circuit  5   b  provides dual-band second harmonic termination. Similar to the description of FIG. 5, the circuit  5   b  in FIG. 6 is a series resonator formed of capacitor  29 , varactor  30 , and inductor  31 , for providing a low impedance at the second harmonic wave. The inductor  31  can be implemented in a lumped form or distributed strip line form. The value of the band-select voltage Vb via inductor  32  is properly selected to set an appropriate capacitance of the varactor  30  for the desired resonant frequency. Again, the high efficiency power amplifier in FIG. 6 is operable in multi-band applications. 
     FIG. 7 is a circuit diagram of a variation of the second embodiment of the present invention. A pin diode  33  is connected between the transmission lines  34  and  35 . The diode is biased by an external band select bias Vb through a bias resistor  36  connected to the anode of diode  33 , and an inductor  37  is connected to the cathode of the diode  33  to provide a DC return path. An RF choke may be substituted for the resistor  36 . When Vb is applied to the diode  33 , the diode is in an active state, which approximately converts the circuit  5   b  to an open transmission line with a length of l1+l2 and a DC de-coupling capacitor  38 . If the length l1+l2 of the transmission line is approximately ⅛ th  wavelength of the lower frequency band f L , then circuit  5   b  provides at the transistor output a low impedance at a second harmonic frequency 2f L . On the other hand, when Vb is removed or zero, the diode is in an off state, which isolates transmission line  35  from transmission line  34  and thus effectively converts the circuit  5   b  to an open transmission line  34  with a length of  11  along with a DC de-coupling capacitor  38 . If the length  11  of the transmission line is approximately ⅛ th  wavelength of the higher frequency band f H , then circuit  5   b  provides a low impedance at the second harmonic frequency 2f H  at the drain terminal. It should be noted that the actual lengths of l1 and l2 are also affected by the pin diode  33 . FIG. 8 is a circuit diagram of another variation of the second embodiment of the present invention. In circuit  5   b , one end of the transmission line  39  is connected to ground, and the other end is connected to a capacitor  40  and then to the drain terminal of the transistor  6 . The junction in which the capacitor  40  and the transmission line  39  are connected together is also connected with a DC de-coupling capacitor  41  and a pin diode  42 , and then to an interior point of the transmission line  39 . The diode  42  is biased by a band-select voltage Vb through a bias resistor  43 . An RF choke may be substituted for the resistor  43 . When Vb is removed or zero, the diode is in an off state, which approximately converts the circuit  5   b  to a series resonator formed of the transmission line  39  and the capacitor  40 . When the length of the transmission line  39  and the capacitor  40  are designed to resonate at the second harmonic 2f L  of the lower frequency f L , the circuit  5   b  provides a low impedance at the drain terminal at the second harmonic wave 2f L . On the other hand, if Vb is applied to the anode of the diode  42 , the diode is in an active state, which approximately reduces the transmission line  39  to an effective length of about l h . The effective length of the transmission line  39  is modified by the capacitor  41  and pin diode  42 . The circuit  5   b  then becomes a series resonator comprising a capacitor  40  and a transmission line with a length of about l h . Since the transmission line  39  has an equivalently shorter length than its physical length, the resonant frequency of the series resonator would be higher than that when the diode is in an off state. Consequently, the circuit  5   b  provides a dual-band second harmonic termination circuit. 
     Although the present invention has been fully described by way of examples with reference to the accompanying drawings, it should be understood that numerous variations, modifications and substitutions, as well as rearrangements and combinations, of the preceding embodiments will be apparent to those skilled in the art without departing from the novel spirit and scope of this invention. For example, a switch other than a diode can be used between the transmission lines, between an interior point of a transmission line and its end point. The transistors can be BJTs, FETs, and the input biasing resistor can be substituted with an RF choke. Also, the phrase “second harmonic frequency termination circuit” is in regard to the second harmonic frequency of a fundamental wave. In addition, although the drawings depict the second harmonic frequency termination circuit (and combined bias circuit) connected to the output of the power transistor, it is also possible to connect the second harmonic frequency termination circuit to the input of the transistor.