Abstract:
A method, arrangement ( 512 ) and communication receiver ( 500 ) for SNIR estimation of a received signal, by: deriving ( 512 A) an estimation {circumflex over (Z)} of SNIR of the received signal in accordance with the relation 
                 Z   ^     =         [     E   ⁢     {          r   ⁡     (   t   )            }       ]     2         E   ⁢     {       r   2     ⁡     (   t   )       }       -       [     E   ⁢     {          r   ⁡     (   t   )            }       ]     2           ,         
where E represents mean value and r(t) represents the level of the received signal; and correcting ( 512 B,  512 C) the estimation {circumflex over (Z)} to produce a corrected estimation Z based on the relation Z=α({circumflex over (Z)})×{circumflex over (Z)}, where α({circumflex over (Z)}) represents a correction factor. The estimation may be corrected by calculating the correction factor, retrieving the correction factor from a predetermined table ( 512 B) or retrieving the corrected estimation from a predetermined table. The correction may be effected by adding to a logarithmic estimation a logarithmic correction factor. This provides the advantage of improved performance under conditions of low signal to noise ratio.

Description:
FIELD OF THE INVENTION 
     This invention relates to signal to noise/interference ratio (SNIR) estimation, and particularly though not exclusively to such estimation in wireless communication receivers. 
     BACKGROUND OF THE INVENTION 
     Many parts of a wireless communications receiver often require an estimation of signal to interference ratio (SIR), signal to-noise ratio (SNR), or (more generically to include SIR and/or SNR) noise plus interference ratio (SNIR). This is needed for purposes of power control, threshold determination for various algorithms, quantisation of soft-decision information for channel decoding purposes to name but a few. 
     A well-known SNIR estimation technique derives its estimated SNIR {circumflex over (Z)} as 
               Z   ^     =         [     E   ⁢     {          r   ⁡     (   t   )            }       ]     2         E   ⁢     {       r   2     ⁡     (   t   )       }       -       [     E   ⁢     {          r   ⁡     (   t   )            }       ]     2               
where E represents mean value and r(t) represents the combination of signal s(t) and noise n(t).
 
     However, this known estimator suffers from a bias term under conditions of low signal to noise ratio. 
     A need therefore exists for SNIR estimation wherein the abovementioned disadvantages may be alleviated. 
     STATEMENT OF INVENTION 
     In accordance with a first aspect of the present invention there is provided a method for SNIR estimation of a received signal, the method comprising:
         deriving an estimation signal {circumflex over (Z)} of SNIR of the received signal in accordance substantially with the relation       

     
       
         
           
             
               
                 Z 
                 ^ 
               
               = 
               
                 
                   
                     [ 
                     
                       E 
                       ⁢ 
                       
                         { 
                         
                            
                           
                             r 
                             ⁡ 
                             
                               ( 
                               t 
                               ) 
                             
                           
                            
                         
                         } 
                       
                     
                     ] 
                   
                   2 
                 
                 
                   
                     E 
                     ⁢ 
                     
                       { 
                       
                         
                           r 
                           2 
                         
                         ⁡ 
                         
                           ( 
                           t 
                           ) 
                         
                       
                       } 
                     
                   
                   - 
                   
                     
                       [ 
                       
                         E 
                         ⁢ 
                         
                           { 
                           
                              
                             
                               r 
                               ⁡ 
                               
                                 ( 
                                 t 
                                 ) 
                               
                             
                              
                           
                           } 
                         
                       
                       ] 
                     
                     2 
                   
                 
               
             
             , 
           
         
       
         
         
           
             where E represents mean value and r(t) represents the level of the received signal; and 
             correcting the estimation signal {circumflex over (Z)} to produce a corrected estimation signal Z based on substantially the relation
 
 Z =α({circumflex over ( Z )})×{circumflex over ( Z )},
 
             where α({circumflex over (Z)}) represents a correction factor. 
           
         
       
    
     In accordance with a second aspect of the present invention there is provided an arrangement for SNIR estimation of a received signal, the arrangement comprising:
         means for deriving an estimation {circumflex over (Z)} of SNIR of the received signal in accordance substantially with the relation       

     
       
         
           
             
               
                 Z 
                 ^ 
               
               = 
               
                 
                   
                     [ 
                     
                       E 
                       ⁢ 
                       
                         { 
                         
                            
                           
                             r 
                             ⁡ 
                             
                               ( 
                               t 
                               ) 
                             
                           
                            
                         
                         } 
                       
                     
                     ] 
                   
                   2 
                 
                 
                   
                     E 
                     ⁢ 
                     
                       { 
                       
                         
                           r 
                           2 
                         
                         ⁡ 
                         
                           ( 
                           t 
                           ) 
                         
                       
                       } 
                     
                   
                   - 
                   
                     
                       [ 
                       
                         E 
                         ⁢ 
                         
                           { 
                           
                              
                             
                               r 
                               ⁡ 
                               
                                 ( 
                                 t 
                                 ) 
                               
                             
                              
                           
                           } 
                         
                       
                       ] 
                     
                     2 
                   
                 
               
             
             , 
           
         
       
         
         
           
             where E represents mean value and r(t) represents the level of the received signal; and 
             means for correcting the estimation {circumflex over (Z)} to produce a corrected estimation Z based on substantially the relation
 
 Z =α({circumflex over ( Z )})×{circumflex over ( Z )},
 
             where α({circumflex over (Z)}) represents a correction factor. 
           
         
       
    
     The arrangement of the invention&#39;s second aspect may be comprised in a communication receiver such as in user equipment or a base station for use in a wireless communication system. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       One method, arrangement and communications receiver for SNIR estimation incorporating the present invention will now be described, by way of example only, with reference to the accompanying drawings, in which: 
         FIG. 1  shows a graphical representation of the probability density function (PDF) of a received binary-valued signal plus noise; 
         FIG. 2  shows a graphical representation of the positive half of the PDF of  FIG. 1 , illustrating distortion of the signal power estimate Ŝ at low signal to noise ratios; 
         FIG. 3A  shows a graphical representation illustrating the relationship of estimated SNIR {circumflex over (Z)} to real SNIR Z; 
         FIG. 3B  shows, similarly to  FIG. 3A , a logarithmic (decibel) graphical representation illustrating the relationship of estimated SNIR {circumflex over (Z)} to real SNIR Z; 
         FIG. 4A  shows a graphical representation illustrating the relationship of a correction factor α({circumflex over (Z)}) to the uncorrected estimated SNIR {circumflex over (Z)}; 
         FIG. 4B  shows, similarly to  FIG. 4A , a logarithmic (decibel) graphical representation illustrating the relationship of the correction factor α({circumflex over (Z)}) to the uncorrected estimated SNIR {circumflex over (Z)}; 
         FIG. 5  shows a block-schematic diagram of a wireless communication system receiver in which the invention is used; and 
         FIG. 6  shows a block-schematic diagram of a UTRA TDD system in which the invention is used. 
     
    
    
     DESCRIPTION OF PREFERRED EMBODIMENT 
     A well-known estimator detects the SNIR of a symmetric binary-valued signal (for example, Binary Phase Shift Keyed—BPSK), under noise of zero mean. The method is also applicable to QPSK (Quadrature Phase Shift Keyed) signals. 
     The method considers a BPSK signal s(t), which may assume the value +/− A. Additive white Gaussian noise (AWGN), denoted n(t), is added to this signal. n(t) has a Gaussian probability density function (PDF) and has a variance (power) of σ 2 . The composite signal plus noise is denoted as:
 
 r ( t )= s ( t )+ n ( t ).
 
     The PDF of r(t) takes the form: 
     
       
         
           
             
               P 
               ⁢ 
               
                 { 
                 
                   
                     r 
                     ⁡ 
                     
                       ( 
                       t 
                       ) 
                     
                   
                   = 
                   y 
                 
                 } 
               
             
             = 
             
               
                 1 
                 
                   
                     2 
                     ⁢ 
                     
                       πσ 
                       2 
                     
                   
                 
               
               ⁢ 
               
                 1 
                 2 
               
               ⁢ 
               
                 
                   { 
                   
                     
                       ⅇ 
                       
                         
                           - 
                           
                             
                               ( 
                               
                                 y 
                                 + 
                                 A 
                               
                               ) 
                             
                             2 
                           
                         
                         
                           2 
                           ⁢ 
                           
                             σ 
                             2 
                           
                         
                       
                     
                     + 
                     
                       ⅇ 
                       
                         
                           - 
                           
                             
                               ( 
                               
                                 y 
                                 - 
                                 A 
                               
                               ) 
                             
                             2 
                           
                         
                         
                           2 
                           ⁢ 
                           
                             σ 
                             2 
                           
                         
                       
                     
                   
                   } 
                 
                 . 
               
             
           
         
       
     
     This PDF is shown in  FIG. 1 . This corresponds to the case of A=30 and σ 2 =400. 
     The SNIR estimation technique uses the following estimator (Ŝ) for the signal power S:
 
 S=E{s   2 ( t )} and  Ŝ≅[E{|r ( t )|}] 2 .
 
     The estimate ({circumflex over (T)}) of the total power (T) of r(t) is:
 
 {circumflex over (T)}=E{r   2 ( t )}.
 
     And so, since r(t)=s(t)+n(t), the noise power N must be equal to the total power minus the signal power:
 
 N=T−S.  
 
     And so the estimate ({circumflex over (N)}) of the noise power N is given by:
 
{circumflex over ( N )}={circumflex over ( T )}−{circumflex over ( S )}= E {r 2 ( t )}−[ E{|r ( t )|}] 2 .
 
     Thus, the signal to noise ratio estimate is: 
     
       
         
           
             
               Z 
               ^ 
             
             = 
             
               
                 
                   S 
                   ^ 
                 
                 
                   N 
                   ^ 
                 
               
               = 
               
                 
                   
                     S 
                     ^ 
                   
                   
                     
                       T 
                       ^ 
                     
                     - 
                     
                       S 
                       ^ 
                     
                   
                 
                 = 
                 
                   
                     
                       
                         [ 
                         
                           E 
                           ⁢ 
                           
                             { 
                             
                                
                               
                                 r 
                                 ⁡ 
                                 
                                   ( 
                                   t 
                                   ) 
                                 
                               
                                
                             
                             } 
                           
                         
                         ] 
                       
                       2 
                     
                     
                       
                         E 
                         ⁢ 
                         
                           { 
                           
                             
                               r 
                               2 
                             
                             ⁡ 
                             
                               ( 
                               t 
                               ) 
                             
                           
                           } 
                         
                       
                       - 
                       
                         
                           [ 
                           
                             E 
                             ⁢ 
                             
                               { 
                               
                                  
                                 
                                   r 
                                   ⁡ 
                                   
                                     ( 
                                     t 
                                     ) 
                                   
                                 
                                  
                               
                               } 
                             
                           
                           ] 
                         
                         2 
                       
                     
                   
                   . 
                 
               
             
           
         
       
     
     The present invention invention is based upon the realisation by the inventor that the above technique suffers from a bias term for low signal to noise ratio. Due to the use of the “absolute-value” operator, the estimate of the signal amplitude (Â) becomes distorted due to the overlap that occurs between the positive and negative portions of the PDF of r(t). Hence the signal power estimate (Ŝ) is also distorted. This is shown in  FIG. 2  for a single signalling state (+1) of amplitude A and power S=A 2 : 
     Portions of the PDF of r(t) that cross the line r(t)=0 (as shown by the line portions  210  and  220 ) are sign-reversed before being accumulated (as shown by the line  230 ) and averaged, and so the estimate of the mean value of r(t) is distorted. In effect, as the signal to noise ratio decreases, so the signal power estimate becomes more over-estimated. The estimate of the total power ({circumflex over (T)}) is however, unaffected. The effect on the overall SNIR estimate is the result of Ŝ appearing in both the numerator and denominator of the equation used to calculate {circumflex over (Z)}. 
     This bias offset however, can be shown to be a direct function of the real signal to noise ratio (Z). Thus, if the relationship between {circumflex over (Z)} and Z is derived and known a priori, then the bias may be removed from {circumflex over (Z)} and the true SNIR (Z) may be recovered. Such correction is the basis of the present invention. 
     The mean value of a signal x(t) is defined as: 
               E   ⁢     {     x   ⁡     (   t   )       }       =       ∫     -   ∞     ∞     ⁢       y   ·   P     ⁢     {       x   ⁡     (   t   )       =   y     }     ⁢     ⅆ   y               
where P{x(t)=y} is the probability of x(t) assuming the value y.
 
     By substituting |r(t)| for x(t) in the above equation, and by integrating only between 0 and ∞ owing to the fact that |r(t)| is positive-valued only, we are able to derive the mean value of |r(t)|. In this case, the probability P{|r(t)|=y} is given by: 
               P   ⁢       {            r   ⁡     (   t   )            =   y     }       y   =     0   -&gt;   ∞           =       1       2   ⁢     πσ   2           ⁡     [       ⅇ       -       (     y   -   A     )     2         2   ⁢     σ   2           +     ⅇ       -       (     y   +   A     )     2         2   ⁢     σ   2             ]             
and so the mean value of |r(t)| is written as:
 
     
       
         
           
             
               A 
               ^ 
             
             = 
             
               
                 E 
                 ⁢ 
                 
                   { 
                   
                      
                     
                       r 
                       ⁡ 
                       
                         ( 
                         t 
                         ) 
                       
                     
                      
                   
                   } 
                 
               
               = 
               
                 
                   ∫ 
                   0 
                   ∞ 
                 
                 ⁢ 
                 
                   
                     y 
                     · 
                     
                       
                         1 
                         
                           
                             2 
                             ⁢ 
                             
                               πσ 
                               2 
                             
                           
                         
                       
                       ⁡ 
                       
                         [ 
                         
                           
                             ⅇ 
                             
                               
                                 - 
                                 
                                   
                                     ( 
                                     
                                       y 
                                       - 
                                       A 
                                     
                                     ) 
                                   
                                   2 
                                 
                               
                               
                                 2 
                                 ⁢ 
                                 
                                   σ 
                                   2 
                                 
                               
                             
                           
                           + 
                           
                             ⅇ 
                             
                               
                                 - 
                                 
                                   
                                     ( 
                                     
                                       y 
                                       + 
                                       A 
                                     
                                     ) 
                                   
                                   2 
                                 
                               
                               
                                 2 
                                 ⁢ 
                                 
                                   σ 
                                   2 
                                 
                               
                             
                           
                         
                         ] 
                       
                     
                   
                   ⁢ 
                   
                     ⅆ 
                     y 
                   
                 
               
             
           
         
       
     
     Evaluating the above integral, the signal amplitude estimate (Â) can be shown to be: 
               A   ^     =     A   ⁡     [     1   +         2     π   ⁢           ⁢   Z         ⁢     ⅇ     -     z   2           -     erfc   (       Z   2       )       ]             
where erfc represents the Complementary Error function and
 
     
       
         
           
             Z 
             = 
             
               
                 
                   A 
                   2 
                 
                 
                   σ 
                   2 
                 
               
               . 
             
           
         
       
     
     Using this last relationship and the fact that 
                 Z   ^     =         A   ^     2         A   2     +     σ   2     -       A   ^     2           ,         
the required relationship between {circumflex over (Z)} and Z can be derived as:
 
               Z   ^     =           [     1   +         2     π   ⁢           ⁢   Z         ⁢     ⅇ     -     z   2           -     erfc   (       Z   2       )       ]     2       1   +     1   Z     -       [     1   +         2     π   ⁢           ⁢   Z         ⁢     ⅇ     -     z   2           -     erfc   (       Z   2       )       ]     2         .           
Z is plotted against {circumflex over (Z)} in the graph of  FIG. 3A .
 
     If the SNIR estimate is expressed in decibels, as is often the case, the graph of  FIG. 3A  becomes that shown in  FIG. 3B . 
     As can be seen, the error in decibels between the estimated SNIR, and the true SNIR becomes appreciable for real SNIR&#39;s of less than approximately 8 dB. This therefore limits the usefulness of this SNIR technique, unless the measurement is corrected. By removing the bias in keeping with this invention (as will be explained more fully below), the usefulness of this SNIR estimation technique can be extended to lower SNIR&#39;s. 
     To remove the bias, we assume that Z can be determined from:
 
 Z =α({circumflex over ( Z )})×{circumflex over ( Z )}
 
where α({circumflex over (Z)}) is a correction factor as a function of the uncorrected SNIR estimate {circumflex over (Z)} and may be determined by plotting {circumflex over (Z)} against (Z/{circumflex over (Z)}) as shown in  FIG. 4A .
 
     α({circumflex over (Z)}) may therefore be either (i) calculated from {circumflex over (Z)} or may be (ii) stored in tabulated form for ‘look-up’ in order to facilitate the evaluation of the true SNIR Z. Alternatively, it will be understood, (iii) a table may hold corrected values of Z and the uncorrected estimated value {circumflex over (Z)} may serve as a pointer to the table to ‘look-up’ the corrected value. It will be understood that all three such correction techniques are different implementations of the same underlying correction scheme based on the corrected SNIR estimate Z being a predefined function (as described above) of the uncorrected SNIR estimate {circumflex over (Z)}. 
     In terms of a logarithmic correction factor Γ{10. log 10 ({circumflex over (Z)})} to be added to 10. log 10 ({circumflex over (Z)}) in order to derive 10. log 10 {Z}, the relationship shown in  FIG. 4B  may be inferred, such that:
 
10. log 10 ( Z )=10. log 10 ( {circumflex over (Z)} )+Γ(10. log 10 ( {circumflex over (Z)} )).
 
     It is recognised that as the SNIR is reduced towards zero, so {circumflex over (Z)} tends asymptotically towards approximately 1.75. At these low SNIR&#39;s, small variations in {circumflex over (Z)} produce large variations in Z. As such, this technique has limitations at very low SNIR&#39;s since a highly accurate measurement of {circumflex over (Z)} is required. This would require a large number of samples to be used in the computation of {circumflex over (Z)} which may not be available in practical circumstances. However, this technique is able to significantly reduce the bias effects of the prior art SNIR estimation technique for the SNIR range between approximately 0 and 8 dB. 
     The corrected estimation technique described above may be used in a receiver in wireless communication system such as UTRA TDD (UMTS—Universal Mobile Telecommunication System—Terrestrial Radio Access in Time Division Duplex mode). Such a receiver, which may be a mobile transceiver unit (commonly referred to in UMTS terminology as User Equipment—UE) or a base station transceiver unit (commonly referred to in UMTS terminology as a Node B) is shown in block schematic form in  FIG. 5 . The transceiver unit  500  contains an antenna  502  coupled to a duplex filter or circulator  504  that provides isolation between receive and transmit chains within the transceiver unit. 
     The receiver chain, as known in the art, includes scanning receiver front-end circuitry  506  (effectively providing reception, filtering and intermediate or base-band frequency conversion). The scanning front-end circuit is serially coupled to a signal processing function  508 , in which the invention may be implemented as will be described in greater detail below. 
     An output from the signal processing function is provided to output  510 , which comprises either: an interface for communicating with a radio network controller if the communication unit is a Node B, or an interface for communicating with (for example) a user display if the communication unit is a UE. 
     The receiver chain also includes a received signal strength indicator (RSSI) module  512  and a controller  514  that operates to a maintain overall control of the different functions and modules of the communication unit  500 . The controller  514  is also coupled to the scanning receiver front-end circuitry 506 and the signal processing function  508  (generally realised by a digital signal processor, i.e. DSP). 
     The controller  514  includes a memory  516  that stores operating regimes, such as decoding and other receiving operations. A timer  518  is typically coupled to the controller  514  to control the timing of operations (transmission or reception of time-dependent signals) within the communication unit  500 . 
     As regards the transmit chain, this includes an input  520 , which comprises either: an interface for communicating with a radio network controller if the communication unit is a Node B, or an interface for receiving user input if the communication unit is a UE. The input  520  is coupled in series through transmitter/modulation circuitry  522  and a power amplifier  524  to the antenna  502 . The transmitter/modulation circuitry  522  and the power amplifier  524  are operationally responsive to the controller. 
     It will be understood that in this embodiment the controller  514  including memory  516  is implemented as a programmable processor, but in other embodiments can comprise dedicated circuitry or any other suitable form. 
     It is noted that corresponding features to those described above with respect to the communication unit  500  are also found in conventional Node B&#39;s. However, the communication unit  500  of this embodiment differs over conventional communication units by virtue that the signal processing function  508  is arranged to implement the corrected estimation technique described above. 
     The signal processing function  508  includes circuitry (not shown) for quantisation of soft-decision information for channel decoding purposes (e.g., using a Viterbi decoder—not shown—to decode symbols in a received signal). Accurate estimation of the SNIR of the received signal improves the accuracy of the soft-decision in respect of decoded symbols, and also enhances the error-correcting ability of the channel decoder. In order to implement the corrected estimation technique described above, the signal processing function  508  includes circuitry  508 A for deriving the received signal&#39;s uncorrected SNIR {circumflex over (Z)}, as known in the prior art described above. Additionally, a table  508 B for looking up the correction factor α({circumflex over (Z)}) (as explained above in relation to  FIGS. 4A and 4B ) is included. The signal processing function  508  also includes a processor  508 C for applying the correction factor to the uncorrected SNIR {circumflex over (Z)} to produce the corrected SNIR Z, as described above. 
     It will be understood that in practice the look-up table  508 B may be provided within the memory  516  in the controller  514 , and that the processor  508 C may be provided by the controller  514 ). It will also be understood that if it is not desired to implement correction of the estimated SNIR by way of a look-up table  512 B, the correction factor α({circumflex over (Z)}) may be calculated (e.g., by the controller  514 ) in accordance with the above-discussed equation: 
     
       
         
           
             
               Z 
               ^ 
             
             = 
             
               
                 
                   [ 
                   
                     1 
                     + 
                     
                       
                         
                           2 
                           
                             π 
                             ⁢ 
                             
                                 
                             
                             ⁢ 
                             Z 
                           
                         
                       
                       ⁢ 
                       
                         ⅇ 
                         
                           - 
                           
                             z 
                             2 
                           
                         
                       
                     
                     - 
                     
                       erfc 
                       ( 
                       
                         
                           Z 
                           2 
                         
                       
                       ) 
                     
                   
                   ] 
                 
                 2 
               
               
                 1 
                 + 
                 
                   1 
                   Z 
                 
                 - 
                 
                   
                     [ 
                     
                       1 
                       + 
                       
                         
                           
                             2 
                             
                               π 
                               ⁢ 
                               
                                   
                               
                               ⁢ 
                               Z 
                             
                           
                         
                         ⁢ 
                         
                           ⅇ 
                           
                             - 
                             
                               z 
                               2 
                             
                           
                         
                       
                       - 
                       
                         erfc 
                         ( 
                         
                           
                             Z 
                             2 
                           
                         
                         ) 
                       
                     
                     ] 
                   
                   2 
                 
               
             
           
         
       
     
     Although in the above example the corrected estimation technique of the invention is implemented for purposes of quantisation of soft-decision information for channel decoding purposes, it may alternatively or additionally be implemented for purposes of power control, threshold determination for various algorithms, etc., and may be implemented at the output of a correlator, a joint detector, or other detector. 
     Referring now also to  FIG. 6 , a UTRA TDD system  600  includes a UE  610  which communicates over a CDMA radio air interface  620  with a Node B  630 . The Node B  630  is controlled by a radio network controller  640 , which communicates with other system infrastructure shown collectively as  650 . Such a system (insofar as it has been described up to this point) is well known and need not be described further. However, it will be understood that the communication unit  500  described above for deriving a corrected SNIR estimation may be advantageously implemented in either a UE  610  or a Node B  630  of the system as shown in the figure. 
     It will be appreciated that the method described above for SNIR estimation of a received signal may be carried out in software running on a processor (such as the processor in which the controller  514  and the memory  516  is implemented), and that the software may be provided as a computer program element carried on any suitable data carrier (also not shown) such as a magnetic or optical computer disc. 
     It will be also be appreciated that the method described above for SNIR estimation of a received signal may alternatively be carried out in hardware, for example in the form of an integrated circuit (not shown) such as an FPGA (Field Programmable Gate Array) or ASIC (Application Specific Integrated Integrated Circuit). 
     In conclusion, therefore, it will be understood that the scheme for SNIR estimation described above provides the following advantages:
         Enables non-biased direct SNIR estimation on a single or binary-valued signal in the presence of additive white Gaussian noise.   Extends the useful range of the method detailed in prior-art into the medium-low SNIR range 0-8 dB, in which the technique detailed in the prior art would suffer significant measurement bias.