Abstract:
A tuned antenna-coupled infrared detector is made possible by application of a bias voltage in the range of a few hundred millivolts. The use of first and second antenna arms connected to the detector makes possible polarization tuning which eliminates the need for bulk-optical polarization filters. An alternative tuned detector is one in which the antenna is frequency tuned by a capacitative device to make the detector particularly responsive to 8 um to 12 um infrared radiation. When integrated into focal plane arrays, these detectors can be used in remote-sensing systems to facilitate enhanced image recognition, feature extraction and image-clutter removal. One preferred version of the polarization tuned antenna has longitudinal metal antenna arms extending outward from an infrared(IR) sensor in a spiral pattern, with polarization tuning devices connected between the antenna arms, and a voltage for controlling the polarization tuning devices, wherein the polarization tuning devices enable real-time control of current distribution in the arms. For the frequency tuned sensors, the embodiment is preferably a microstrip antenna coupled to a bolometer wherein the sensor has a tunable response accomplished by use of a single substrate voltage on a separate capacitative device. The infrared(IR) sensors can be tunnel diodes, schottky diodes, photovoltaics, photoconductors, bolometers and pyroelectrics. Application areas can include earth-resource mapping, pollution monitoring, and general surveillance.

Description:
This invention relates to infrared detectors, and in particular to an antenna, which includes a device coupled directly to the antenna feed which allows tuning of the collected infrared radiation onto an infrared detector sensor, and is a Continuation-In-Part of U.S. Application Ser. No. 09/004,132 entitled: Polarization-Tunable Antenna-Coupled Infrared Detector, filed on Jan. 7, 1998 now U.S. Pat. No. 6,037,590 issued on Mar. 14, 2000, which claims the benefit of priority to U.S. Provisional Application No. 60/048,334 filed May 30, 1997. 
    
    
     BACKGROUND AND PRIOR ART 
     Infrared(IR) systems have been widely used in the past. Current systems generally require bulk optical systems having multiple moving parts for polarization control. Image forming radiation is typically collected for a fixed polarization state. Optical filters must be used in the optical train before the receiving detector array. The selection of the polarization state requires mechanical motion of the optical filters. The typical weight of the necessary filter and switching assemblies is on the order of 1 kg or more. The required time to switch between polarization states can be on the order of 2 seconds or more. Polarization-resolved imagery is largely unexploited, because of inconvenient implementation. 
     Many U.S. Patents have been proposed for Infrared detectors but have many of the problems previously described. See for example U.S. Patents: U.S. Pat. No. Re. 30,131 to Javan; U.S. Pat. No. 4,652,885 to Saffold et al.; U.S. Pat. No. 5,239,179 to Baker; U.S. Pat. No. 5,248,884 to Brewitt-Taylor et al.; U.S. Pat. No. 5,404,146 to Rutledge; U.S. Pat. No. 5,432,374 to Norton; U.S. Pat. No. 5,436,453 to Chang et al.; U.S. Pat. No. 5,442,176 to Eckel, Jr. et al.; U.S. Pat. No. 5,446,284 to Butler et al.; U.S. Pat. No. 5,512,750 to Yanka et al.; U.S. Pat. No. 5,519,529 to Ahearn et al.; and U.S. Pat. No. 5,523,570 to Hairston. 
     SUMMARY OF THE INVENTION 
     The first objective of the present invention is to provide an Infrared(IR) detector antenna system for collecting image-forming radiation by means of a tuned state. 
     The second object of this invention is to provide an IR detector antenna system of collecting radiation in a dynamically programmable tuned state. 
     The third object of this invention is to provide an IR detector antenna system where optical filters are eliminated and polarization selection is integrated directly onto the detector array. 
     The fourth object of this invention is to provide an IR detector antenna system where the control and selection of the tunable state is completely electronic and requires no moving parts. 
     The fifth object of this invention is to provide an IR detector antenna system where the weight required for implementation is essentially zero. 
     The sixth object of this invention is to provide an IR detector antenna system where the time required to switch polarization is compatible with video frame rates on the order of approximately {fraction (3/1000)} of a second. 
     The seventh object of this invention is to provide an IR detector antenna system where the polarization state for reception can be tailored to features of interest in the image data. 
     The eighth object of this invention is to provide an IR detector antenna system which enables the development of improved algorithms for both image-recognition and for discrimination against image clutter. 
     In the polarization tuned embodiment of the subject invention, infrared antennas are integrated into existing Infrared(IR) focal-plane-array (FPA) systems. The arrangement is an array of independent antenna-coupled detectors, rather than a phased-array antenna. Each novel detector pixel square can have exterior dimensions of between approximately 40 micrometers to approximately 50 micrometers on each side. The size of the array can be approximately 5 to approximately 20 mm across each side. One possible embodiment of an individual pixel (unit cell) includes a series connection of individual antenna-coupled infrared sensors distributed over the unit cell. 
     The polarization tuning is accomplished by the fact that the relative phase of the current waves on the arms of each antenna is determined by the capacitance of the load impedance located at the feed. 
     The frequency tuning embodiment of the invention relies on the electrical size of the antenna (how large is the antenna in terms of the wave-length of the radiation to be sensed) which is modified by external means whereby its resonant frequency is changed. 
     The capacitance of the IR sensing diode used at the feed is a function of the externally applied voltage imposed on the antenna. 
     The polarization response of the sensor can thus be controlled electronically, eliminating the need for separate optical filters. 
     For the frequency tuned sensors, this embodiment is preferably a microstrip antenna coupled to a bolometer wherein the sensor has a tunable response accomplished by use of a single substrate voltage on a separate capacitative device such as a MOS(Metal Oxide Semiconductor). 
     These detectors and their arrays can be used in remote-sensing systems to facilitate enhanced image recognition, feature extraction, and image-clutter removal. The application areas can include earth-resource mapping, pollution monitoring and general surveillance. 
     Further objects and advantages of this invention will be apparent from the following detailed description of the two preferred embodiments which are illustrated schematically in the accompanying drawings. 
    
    
     BRIEF DESCRIPTION OF THE FIGURES 
     FIG. 1A is a top view of a single antenna-coupled sensor. It is one sub-unit of the pixel. Pixels (FIG. 3) are arranged into focal-plane arrays (FIG.  4 ). 
     FIG. 1B is an enlarged side view of the contact region between the first and second antenna arms of FIG. 1A, along arrow A. 
     FIG. 2A shows the foundation of the polarization switching behavior for a balanced mode in the Antenna-coupled sensor of FIGS. 1A-1B. 
     FIG. 2B shows the foundation of the polarization switching behavior of the subject invention for an unbalanced mode in the antenna-coupled sensor of FIGS. 1A-1B. 
     FIG. 3 a single pixel of the focal plane array shown in FIG.  4  and is composed of a series connection of individual antenna-coupled sensors shown in FIG.  1 . 
     FIG. 4 is a focal plane array, composed of a matrix of individual pixels, each consisting of a series connection of antenna coupled sensors. 
     FIG. 5 is an enlarged view of an actual embodiment of the subject invention. 
     FIG. 6 is an measured plot of the demonstrated tuning of polarization angle as a function of applied bias voltage. 
     FIG. 7 shows a typical application of the subject invention. 
     FIG. 8 a  shows the top view of a microstrip antenna intgrated bolometer. 
     FIG. 8 b  illustrates the antenna of FIG. 8 a  as a transmission line model. 
     FIG. 9 the top view of an antenna intgrated bolometer. 
     FIG. 10 illustrates a top view of the frequency tuned device. 
     FIG. 11 shows the side view of the bolometer configuration. 
     FIG. 12 shows the side view of the MOS capacitor configuration. 
     FIG. 13 shows the side view of the ground plane contact pad configuration. 
     FIG. 14 shows the side view of the top contact pad configuration. 
     FIG. 15 shows the plot of MOS capacitance versus bias voltage. 
     FIG. 16 shows of sensor responses versus incident wavelength for various imposed capacitances. 
     FIG. 17 shows exemplary circuit using the bolometer of the subject invention. 
    
    
     DETAILED DESCRIPTION 
     Before explaining the disclosed embodiment of the present invention in detail it is to be understood that the invention is not limited in its application to the details of the particular arrangement shown since the invention is capable of other embodiments. Also, the terminology used herein is for the purpose of description and not of limitation. 
     First Preferred Embodiment 
     FIG. 1A is a top view of a single antenna-coupled sensor  1 . It is one sub-unit of the pixel. Pixels (FIG. 3) are arranged into focal-plane arrays (FIG.  4 ). FIG. 1B is an enlarged side view of the contact region between the first and second antenna arms of FIG. 1A, along arrow A. Referring to FIGS. 1A-1B, the individual wires  10 ,  20  of the antenna  1  are made of metal (such as but not limited to aluminum, gold, nickel, etc.). The wires  10 ,  20  have a length approximately equal to one half of the wavelength of the radiation incident on the antenna  1 . 
     Referring to FIGS. 1A-1B, antenna  1  is lithographically fabricated on top of a transparent substrate material  50  such as silicon. Antenna  1  is generally illuminated through the dielectric substrate  50 , then the relevant wavelength (as far as the length of the arms is concerned) is the wavelength of the radiation inside the substrate  50 . This is the free-space wavelength of 10 micrometers (infrared) and for example, in a silicon substrate the substrate wavelength is around 3 micrometers. 
     Referring to FIGS. 1A-1B, the incident electromagnetic radiation will induce infrared-frequency (on the order of 30 THz) current waves to flow in the arms  10 ,  20  of the antenna  1 , along the direction of the incident electric field(the electric field of incident radiation has an arbitrary in-plane orientation.). The induced current waves will propagate along the antenna wires  10 ,  20 , producing an infrared-frequency voltage across the sensor material. This is the mechanism for capturing the incident radiation. Sensor material  15  can include but is not limited to tunnel diodes such as NiO and AlO. Sensor material  15  can further include schottky diodes such as but not limited to PtSi, NiSi, and IrSi. Sensor material  15  can further include photovoltaic materials such as but not limited to Si, LnSb, and HgCdTe. Sensor material  15  can further include photoconductive materials such as but not limited to PbSe, PbS, Si, InSb, and HgCdTe. Sensor material  15  can further include pyroelectric materials such as but not limited to LiTaO 3 . Antenna arms  10  and  20  can be metal wires with a small in-plane width compared to the wavelength of the incident radiation (See FIG. 5, i.e. approximately 2 micrometers). 
     Referring to FIGS. 1A-1B, the infrared sensor material  15  constitutes a load impedance of nominally 100 ohms across the contact region of the antenna  1 , seen in the side view of FIG.  1 B. For diode sensors, the current waves are rectified by the nonlinear current-voltage characteristic (FIG.  5 ), causing a change in the dc resistance. This dc resistance is read out by means of a voltage bridge circuit  35 ,  37  having a value of approximately +/− approximately 100 millivolts across a load resistor  38  of approximately 100 ohms between the dc connection  29  and variable bias voltage  34  of +/− approximately 200 millivolts in antenna  1 . Lines  32  and  39  connect antennas  19 ,  29  to the bridge circuit. Other types of infrared sensor materials can also be used in the configuration of FIGS. 1A-1B. For example, bolometric sensors will dissipate the current waves, causing a temperature rise in the bolometer, and a change in the dc resistance. 
     The polarization-tuning mechanism arises because the impedance presented to the antenna  1  is not a pure resistance. Particularly in the case of diode sensors, the impedance has an inherent capacitive component caused by the semiconductor junctions inherent in the construction of the diode. These junctions have a capacitance that is a function of the applied voltage. This voltage is supplied across the dc connections  19 ,  29  of the antenna  1 . 
     The ability to change the capacitance of the sensor by changing the externally applied bias voltage is the key to tuning the polarization of the antenna-coupled sensor. Referring to FIGS. 1A-1B, antenna arms  10  and  20  constitute a transmission line. In any such structure, the load impedance will determine the phase relationship between the current waves that can be excited on the line. 
     FIG. 2A shows the foundation of the polarization switching behavior for a balanced mode. FIG. 2B shows the foundation of the polarization switching behavior of the subject invention for an unbalanced mode. These two modes have a different polarization signature, shown as the dotted line. The mixing between these two modes and the resulting net polarization state of the IR sensor is determined by capacitance of the contact A, which is dependent on the bias voltage applied across the dc contacts  19 ,  29 . FIGS. 2A-2B, considers only the two primary current-wave modes that propagate on the antenna arms  10 ,  20 . When the current waves are 180 degrees out of phase at the contact A, this is called a balanced mode. The situation when the current waves are in-phase at the contact is called an unbalanced mode. These two modes of FIGS. 2A,  2 B have a polarization response that is 90 degrees apart. Any phase between the current waves that is not zero or 180 degrees can be expressed as a sum of these two modes. The polarization response for these intermediate conditions can be similarly expressed as a sum of the two polarization states. The angle of the polarization response, seen as the vector sum of the directions of the two current waves, will depend on the mixture of the two modes. It has been demonstrated previously in published research by one of the subject inventors that the polarization response of an infrared antenna  1  depends on this phase relationship. See “Polarization response of asymmetric-spiral infrared antennas,” Applied Optics, Vol. 36, pp 6485-6490 (Sep. 1, 1997). The phase difference is determined by the capacitance of the contact impedance, which can be controlled by the external bias voltage. Thus the external bias voltage controls the mode mixture and hence the polarization response of the sensor. 
     FIG. 3 is a single pixel  200  of the focal plane array shown in FIG.  4  and is composed of a series connection of individual antenna-coupled sensors  1  shown in FIG.  1  and other individual antenna-coupled sensors  100  to (100+n), and (101+n). These individual sensors are electrically connected in series to constitute one pixel  200 . Such a series connection will allow an external bias voltage to be applied at nodes  210 ,  220  across all sensor elements  1 , 100 to (100+n), and (101+n) simultaneously, controlling the polarization response of all sensors elements. Because the sensors are subwavelength in dimension, the series connection will also provide an enhanced collection efficiency, compared to one sensor  1  alone. The signals from each sensor  1 , 100 to (100+n), and (101+n) in the pixel  200  will also add in this configuration, providing an increased signal level (proportional to the number of elements in series) compared to a single sensor  1 . Component  50  refers to the substrate such as but not limited to silicon and the like, similar to substrate  50  shown in FIG.  1 A. The pixel  200  is read out as a unit, providing a measurement of the radiation that falls on the pixels as a whole. A pixel  200  will typically be a square of dimension 40 to 50 microns on one side (approximately 5 wavelengths of the incident radiation). 
     These pixels will be arranged in a focal plane array  300 , seen in FIG.  4 . The focal plane array  300  can be placed in the image plane of an optical system. The arrangement and readout of individual pixels are capable of forming resolved images of the radiation that falls on the array. A focal plane array  300  can contain a matrix of between approximately 128 to approximately 512 pixels on a side, yielding focal plane array dimensions of approximately 5 to approximately 25 millimeters on a side. 
     The subject inventors has demonstrated polarization tuning on an individual antenna-coupled infrared sensor of the type described in  Applied Optics  Vol. 36, pp 6458-6490, 1997. FIG. 5 is an enlarged magnified view of the antenna  1 , wherein approximately one inch pictured is equivalent to approximately {fraction (1/30,000)} of the an inch. The antenna  1  used for this demonstration was Nickel on Silicon in a spiral configuration, with the arms  10 ,  20  closest to the contact region intersecting at a 90 degree angle, as seen in FIG.  1 A. Elements  10 ,  19 ,  20  and  29  correspond to like components described in reference to FIGS. 1A-1B. The sensor  15  (shown more clearly in FIG. 1B) was a metal-metaloxide-metal (MOM) diode, of the type described in “Nanometer thin-film Ni—NiO—Ni diodes for 30 THz radiation”,  Applied Physics,  Vol. A 58, p. 329-342, 1994. The capacitance of the contact area (of dimensions approximately 0.25 micrometer on a side) is on the order of 0.1 nanofarads. It is estimated that a change in bias voltage from approximately −160 millivolts to +160 millivolts changes the capacitance of the sensor(contact A) 15 by at least a factor of two. 
     The polarization angle was measured using a procedure similar to that described in  Applied Optics  Vol. 36, pp 6485-6490, 1997. When the bias voltage was varied between approximately −160 millivolts to approximately +160 millivolts, the polarization angle of the detector  1  tuned continuously and repeatably from 113 degrees to 25 degrees, demonstrating a total tuning range of approximately 88 degrees. This measured polarization tuning data is shown in FIG. 6, which shows that a range of polarization tuning is possible that is sufficient to encompass both vertical and horizontal polarization. This flexibility allows for radiation reception in an selected polarization state. 
     The invention facilitates the development of compact, no-moving parts, imaging polarimeters. Having the polarization tuning mechanism integrated directly onto a chip will eliminate a large portion of the optical systems that are otherwise required for polarization resolved imaging. 
     Furthermore, the subject invention allows passive infrared sensors to have improved feature extraction, discrimination and clutter removal. The tuning accomplished by the invention is substantially faster using electrically controlled antennae than using bulk optics. One-frame-at-a time tuning allows for faster algorithms to be implemented giving more complex capabilities in real-time, such as differentiation of man-made targets from foliage. 
     FIG. 7 shows a typical application  400  of the subject invention where the focal-plane array of antenna-coupled detectors  300  (FIG. 4) receives radiation  490  from the field of view of a target scene  475  such as an earth surface, weaponry and the like, with a typical optical system  450  such as but not limited to an infra-red (IR) transmitting lens such as silicon and zinc selenoid. Such an application  400  can be used for remote sensing such as earth resource mapping, pollution monitoring, surveillance and the like. 
     Second Preferred Embodiment 
     In this embodiment, tuning is realized by modifying the wavelength of the antenna so it is responsive to incident radiation by a voltage-controlled capacitor. A microstrip antenna is used to couple the incident infrared radiation to a bolometer. As indicated the antenna is tuned so as to provoke a tunable response in the sensor for the approximately 8 to 12 micrometers wavelength region of the infrared. This tuning is accomplished by use of a single substrate voltage. Construction of the device uses planar technology that is compatible with standard silicon processes for electron-beam fabrication. 
     In this novel approach to IR detection, an antenna is used to improve their radiation collection ability with separation of this collection function from the detection function. Since the detectors are resonant structures, electronic means has been realized to alter their resonant frequency and thereby achieve frequency tunability with resultant enhanced responsivity to the incident radiation of the wavelength spectrums to be detected. The idea behind frequency tuning is to modify the electrical size of the antenna by said electronic means and thus change its resonant frequency. 
     Since it has been found that a narrow bandwidth antenna is required to achieve frequency tunability, a microstrip antenna has been used because of its inherent narrow bandwidth. Other characteristics that make it attractive is that the microstrip antenna has a low profile, is light weight, simple to manufacture, has low cost and easily integrated with circuits. 
     A representative microstrip antenna is pictured in a top view of an IR detector in FIG. 8 a  where the antenna  81  of width  82  (3.0 micrometers) and length  83  (2.3 um) is integrated with the bolometer  84  separated from the MOS detector  85 . 
     The microstrip patch antenna is electronically portrayed in FIG. 8 b  as a half wavelength uniform transmission line  86  imposed in an effective (consider the fringing effect) dielectric. The characteristic impedance (Z) and propagation constant (G) are determined by the antenna width, dielectric thickness and its dielectric constant. The transmission line  86  is terminated with a RC parallel combination  87  at both ends. Its electrical length can be altered by terminating it with a reactive load, e.g., a capacitor  88  increases the length while an inductor shortens the line. In our embodiment, a variable capacitor  88  is connected across the antenna open end. 
     FIG. 9 again shows in larger representation the top view of the antenna of FIG. 8 a  with a line  89  to the contact pad (not shown) but illustrated in FIG. 10 with width dimensions  90  of approximately 250 micrometers across each side of said contact pads  91 ,  93 . 
     The physical embodiment of the frequency tunable antenna coupled IR detector is shown in the views of FIGS. 11 through 14. FIG. 11 shows a side view of the antenna coupled bolometer of FIG. 9 along arrows A, B. FIG. 12 shows the MOS (Metal Oxide Semiconductor) view of FIG. 9 along arrows C, D. FIG. 13 shows the ground plane view of FIG. 10 along arrows E, F. FIG. 14 shows the top contact view of FIG. 10 along arrow G, H. FIG. 17 shows a basic circuit using the bolometer antenna, with V bias, photons being emitted toward the bolometer, the change in resistance at the bolometer is the sensor, and a voltage output (Voutput) across a resistor (Rload) can be measured by a standard voltmeter. 
     Referring to FIGS. 8 a  and  9 - 14 , an illustrative microstrip patch antenna  81  is aluminum having a rectangular shape with a width  82  of approximately 3.0 micrometers, a length  83  of approximately 2.3 micrometers and a thickness of approximately 0.2 micrometers and supported by a silicon substrate  92  of approximately 0.2 micrometers thickness and having a dielectric constant of approximately 3.8. The silicon substrate  92  in turn is supported by an approximately 0.2 micrometers thick ground plane  93  of aluminum disposed on a p-type silcon substrate  94  of approximately 15 mils thickness and having a resistivity of approximately 250 Ohm-cm. Now that the physical structure of the tunable IR detector has been disclosed, its fabrication begins with the deposition by electron beam of an approximately 200 NM-thick aluminum layer (the ground plane  93 ) onto the surface of the silicon substrate  94 . A hole is then etched (electron beam lithography and reactive ion etch) into the aluminum layer for the MOS capacitor. The antenna substrate  92  of silica is deposited on the ground plane  93 . The bolometer  84  and contact pad  91  windows are opened in the silica layer, a niobium layer is then deposited and the bolometer  84  is defined by electron beam lithography and liftoff. A new approximately 200 nm-thick aluminum layer is deposited, the patch antenna  81 , line  89  and contact pads  91  are defined by electron beam lithography and liftoff and finally an approximately 1,000 nm-thick aluminum is deposited after which thick contact pads  91  are defined. 
     Frequency tuning is achieved by altering the electrical length of the microstrip antenna with the aid of a MOS capacitor  85  since MOS capacitance is voltage dependent. FIG. 15 shows the voltage dependent MOS capacitance as MOS capacitance versus bias voltage. The MOS capacitance is comparable with the open end capacitance of the microstrip antenna (about 5 e-5 pF). assuming a substrate resistivity of approximately 250 Ohm-cm, the MOS capacitance at zero bias is approximately 1.6 e-4 pF per square micron. Therefore, one needs about one square micron for the surface of the MOS capacitor (see FIG. 9 at  85 ). 
     FIG. 16 shows the predicted approximately 8 um to approximately 12 micrometers wavelength tuning of the above embodiment wherein there is shown the normalized sensor response as a function of the wavelength. This behavior is predicted using a commercial method of moments simulation package (IE3D from Zeeland Sotware, Inc.). To cover the entire 8-12 micrometers range, the capacitance needs to be increased by a factor of five. An examination of FIG. 15, indicates that such a capacitance change seems to be achievable. 
     Frequency tuning of a microstrip antenna for capture of an approximately 8 um to approximately 12 um wavelength radiation is realized utilizing capacitance change in response to bias voltage change of a MOS capacitor. The detector for IR radiation can be a niobium bolometer connected between the patch antenna and the ground plane of the device. 
     While the invention has been described, disclosed, illustrated and shown in various terms of certain embodiments or modifications which it has presumed in practice, the scope of the invention is not intended to be, nor should it be deemed to be, limited thereby and such other modifications or embodiments as may be suggested by the teachings herein are particularly reserved especially as they fall within the breadth and scope of the claims here appended.