Abstract:
A noise inverter circuit substantially reduces the effects of noise generated within power lines operating as a communication media. Input noise signals are clipped to reduce the noise wave amplitude and the peak amplitude is inverted to a value less than the signal amplitude. By limiting the positive rate of change of peak signal amplitude, the prevailing signal level is averaged over a longer time base than the duration of the noise wave.

Description:
BACKGROUND OF THE INVENTION 
     Power line communication systems are employed for carrying signals between transmitters and receivers interconnected by means of the line and neutral conductors. Since the line conductor continuously carries current, noise is occasionally generated by sudden interruptions in current caused by various switching devices. 
     U.S. Pat. No. 4,433,326 and U.S. Pat. No. 4,408,186 describe power line communication systems wherein signals are generated between the neutral and ground conductors. Since the neutral conductor is a continuous current carrier, some noise is generated which could interfere with the communication signals. The complex nature of the noise waveform requires sophisticated filter circuits to reduce the noise amplitude to below the level of the signal amplitude. 
     The purpose of this invention is to provide a noise inverter circuit for reducing the noise amplitude as well as providing automatic tracking of the threshold for noise inversion to the prevailing signal level. 
     SUMMARY OF THE INVENTION 
     A noise inverter circuit dynamically inverts the peaks of the signal waveform which includes noise such that the amplitude of the fundamental is equal to or less than the signal amplitude. A sudden increase in noise signal amplitude turns on a pair of transistors on alternate polarity peaks. The transistor current is increased to produce a corresponding reduction in the peak output voltage. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is a graphic representation of the signal and noise waveforms generated within a power line communication system; 
     FIG. 2 is a graphic representation of the waveforms depicted in FIG. 1 with the noise peak amplitude clipped to a level equal to signal amplitude; 
     FIG. 3 is a graphic representation of the waveforms depicted in FIG. 2 after inverting the clipped noise amplitude in accordance with the noise inversion circuit of the instant invention; 
     FIG. 4 is a circuit representation of a first embodiment of the noise inverter circuit according to the invention; and 
     FIG. 5 is a second embodiment of the noise inverter circuit according to the invention. 
    
    
     DESCRIPTION OF THE PREFERRED EMBODIMENT 
     FIG. 1 shows a characteristic signal waveform B when the information is in the form of a modulation of a higher frequency carrier signal. One such means of information transfer comprises amplitude shift keying (ASK) wherein digital data is derived from a 100% amplitude modulated carrier signal. When employed for communication over power systems, a typical carrier frequency of 150 KHZ is usually employed. As described in the aforementioned U.S. patents, which are incorporated herein for purposes of reference, impulse type noise such as that shown at A in FIG. 1 is created by both mechanical and solid state switches. Noise waveform A is typically a damped sinusoid having a much larger amplitude than carrier signal B and may also have a ringing frequency within the passband of the receiver filters. A typical parallel resonant receiver filter, when subjected to a ringing noise waveform such as A, greater than signal waveform B, and at the same frequency, produces a ringing output waveform larger than B having an exponential decay inversely related to the bandwidth of the receiver filter. 
     One means of reducing the amplitude of noise waveform A is to clip or limit the amplitude of the noise waves to equal the peak signal amplitude of signal waveform B. This is shown at A&#39; in FIG. 2 wherein the amplitude of waveform A is clipped to a value approximately equal to that of the amplitude of signal waveform B. However, the amplitude of the fundamental frequency component of clipped noise waveform A&#39; is still some 41% greater than a sine wave configuration having the same peak amplitude. This invention provides a technique for dynamically inverting the peaks of the limited waveform A&#39; in such a manner that the amplitude of the fundamental frequency component is equal to or less than the amplitude of signal waveform B. FIG. 3 shows a resulting noise waveform A&#34; after clipping and inverting according to the technique of the instant invention compared to the signal waveform B. 
     A noise inverter circuit 10 for providing the inverted noise waveforms A&#34; of FIG. 3 is shown in FIG. 4 and is designed for signal amplitudes in the order of one or two volts. An input voltage V 1  is derived from the power line within a residential or commercial building, as described within the aforementioned U.S. patent applications, for example, by capacitive coupling a receiver with the neutral and ground conductors. The voltage waveform appearing at voltage input V 1  is similar to that shown in FIG. 1. Capacitors C 1  and C 2  become charged to peak signal magnitude through diodes D 5 , D 6  and resistor R 4  on alternate polarity peaks and are continually discharged through resistor R 3 . A sudden increase in signal input, such as that depicted by the amplitude of noise waveform A in FIG. 1, results in a higher charging current increasing the voltage drop across resistor R 4  to turn on transistors Q 1 , Q 2  on alternate polarity peaks. The collector currents of transistors Q 1 , Q 2  flowing through R 2  reduce the peak output voltage appearing at V 2  and tend to limit the peak voltage applied to C 1  and C 2 . At high peak signal voltage input at V 1 , caused by the occurrence of noise, the voltage drop across R 2  permits conduction of diodes D 1 , D 2  or D 3 , D 4 , thereby limiting the peak voltage applied to C 1  and C 2 . In the arrangement shown in FIG. 4, resistor R 1  is connected with one of the input terminals and with the anode of D 1 , the cathode of D 3 , one side of resistor R 2  and with one side of each of the capacitors C 1  and C 2 . The cathode of D 1  is connected in series with the anode of D 2  which is connected with the anode of D 4 . The cathode of D 4  is connected in series with the anode of D 3 . The other side of R 2  is connected with the collector of transistor Q 1  and the emitter of Q 1  is connected to the other input terminal. The base of Q 1  is connected with the anode of diode D 5 , one side of resistor R 3  and the other side of capacitor C 1 . The cathode of D 5  is connected through resistor R 4  to the emitters of Q 1  and Q 2 , directly connected with the anode of diode D 6 . The cathode of D 6  is connected with the other side of resistor R 3 , the other side of capacitor C 2  and the base of transistor Q 2 . The emitter of Q 2  is connected to one of the output terminals and the collector Q 2  is connected with the other output terminal. 
     The circuit 10 depicted in FIG. 5 is for lower information signal amplitudes than that of FIG. 4, typically in the 0.1 to 0.2 volt range. Similar circuit elements are employed and common reference numerals depict similar functions. 
     An operational amplifier, AMP, is employed to permit operation at lower levels. One side of R 1  is connected to one of the input terminals and the other side of R 1  is connected in common with the collectors of Q 3  and Q 4 , one side of R 2  and to one input of the amplifier. The other input to the amplifier is connected to ground through R 7  and the output of the amplifier is connecter in common with one side of each of the capacitors C 1  and C 2  and to R 7  through R 8 . Resistors R 7  and R 8  are used to define the voltage gain of the amplifier. The other side of capacitors C 1  and C 2  are connected together by means of resistor R 3 . C 1  is connected to the anode of D 5  and C 2  is connected to the cathode of D 6 . The cathode of D 5  is connected to the anode of D 6 , and, through resistor R 4 , to one side of each of the resistors R 5  and R 6  and to the emitters of Q 3  and Q 4 . The other side of R 5  is connected to the emitter of Q 1  and the other side of R 6  is connected with the emitter of Q 2 . The collector of Q 2  is connected with the other side of R 2  and with one of the output terminals. The other output terminal is connected in common with the emitters of Q 4  and Q 3 , and with resistors R 4  and R 6 . The circuit of FIG. 5 operates in a similar manner to that described earlier with reference to FIG. 4. The operational amplifier increases the signal magnitude prior to charging Capacitors C 1  and Capacitors C 2  to the prevailing peak signal magnitude through diodes D 5  and D 6 . The transistors Q 3 , Q 4  are provided to limit the charging voltage. 
     The circuits described in FIGS. 4 and 5 are especially effective for reducing noise in power line communication systems when the information signal is in digital form and amplitude shift keying is employed as a means of modulation. The circuits can be discrete circuit components connecting between the receivers and the power line as described earlier, or can be incorporated within the receiver circuit.