Abstract:
A high-frequency power transistor is suggested in which the emitter and base contacts, as well as the collector contacts, occur in a principle plane on the silicon layer. A metallization can be arranged on the oppositely located second principle plane, which enables a connection with the heat sink in an easy manner. Shield grids can be provided within the substrate in order to compensate for the effect of unwanted depletion-layer diodes to a great extent.

Description:
PRIOR ART 
     The invention is directed to a high-frequency power transistor using bipolar epitaxy technique and having a plurality of emitters with emitter and base contact strips arranged in its base region, the emitter and base contacts are located at a main surface of the silicon layer. 
     High-frequency transistors for power output stages in high-frequency amplifiers are usually produced with the epitaxy technique. In known constructions, they are usually insulated against the heat sinks, which are conventionally connected to ground, with thin beryllium oxide layers because of the good heat conductivity. However, this isolation technique is not only expensive, but is also critical with respect to handling, since beryllium oxide is poisonous. 
     In addition, it is known to construct transistors in monolithic integration technology, wherein the individual components of such a semiconductor arrangement are isolated relative to one another and to the substrate by means of depletion or barrier layers, possibly also dielectric layers of SiO. 
     However, the losses of the depletion layer insulation increase as the operating frequency increases, since the depletion layer capacitances which are formed are loaded with ohmic bulk resistors. For this reason, the previously known monolithically integrated transistors are unsuitable in practice as high-frequency power transistors. 
     ADVANTAGES OF THE INVENTION 
     In contrast, the high-frequency power transistor of the invention has the advantage that an isolating intermediate layer which is applied during the wafer production process, can comprise a depletion or barrier layer, but preferably comprises a dielectric such as an oxide or a nitride layer, and is accordingly inexpensive and easy to use. An alloyable or solderable coating can be applied to this layer, which enables a connection with a heat sink. This is made possible in that the emitter, base and collector electrodes lie on the other main surface of the silicon layer, wherein the base region and the emitter contact strips are arranged between collector contact strips. This measure enables a simple, inexpensive production of a high-frequency power transistor, wherein the oxide or nitride layers can be deposited on the silicon as an intermediate layer using the plasma method during the wafer production process. A polysilicon layer can be applied additionally to the intermediate layer as alloyable coating. An aluminum nickel layer can serve as solderable coating, wherein a gold layer can be applied additionally as surface protection. 
     The heat sink connected with the transistor can be connected to ground relative to high frequency, but preferably also relative to direct current. 
     In order to prevent reflected capacitances, it is advantageous to arrange a highly doped shield grid in the silicon under the base connection lines and under the base contact spot, respectively, which shield grid is connected to ground potential at least relative to high frequency. 
     In order to create permanent defined conditions at the circumference of the semiconductor layer, it is also advantageous to provide an isolating diffusion region having the same doping as the substrate at least at the locations not connected to ground. The correspondingly constructed regions are accordingly passivated. 
     In order to stabilize the current distribution, resistors can be diffused into the feed lines to the individual emitter fingers, wherein these resistors can be formed by means of highly doped n-regions. 
    
    
     DRAWING 
     The invention is explained in more detail in the following description and with the aid of the drawing, in which: 
     FIG. 1 shows the equivalent circuit diagram of a known bipolar monolithically integrated high-frequency transistor; 
     FIG. 2 shows the equivalent circuit of a monolithically integrated high-frequency transistor with an additional substrate diode according to the invention; 
     FIG. 3 shows the equivalent circuit of a monolithically integrated high-frequency transistor with shield grid and corresponding oxide capacitance; 
     FIG. 4 shows a top view of a monolithically integrated high-frequency transistor; 
     FIG. 5 shows a side view the section AB of the arrangement shown in FIG. 4; and 
     FIG. 6 shows a section AB of the arrangement shown in FIG. 4, but with a diffused-in deep collector, instead of the isolating diffusion, as a shield grid. 
    
    
     DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     FIG. 1 shows an equivalent circuit of a high-frequency transistor 1 with emitter contact 2, base contact 3 and collector contact 4. The bulk resistors 5, 6 and 7 are indicated in the connection lines. The emitter bulk resistor 5 is increased at least by means of additional stabilization resistors which are assigned to every partial emitter. However, in the present equivalent wiring diagram, the illustration of such additional components and of inductances and parasitic capacitances is omitted. 
     If the high-frequency transistor 1 is constructed with monolithic integration technique, the depletion layer capacitance 9 of the substrate diode 10, with its loss producing series resistor 8, appears in addition. 
     The depletion layer capacitance 9 of the substrate diode 10 and the losses in the series resistor 8 can now be reduced by means of a structure diverging from the usual structures of monolithically integrated circuits. This principle is shown in FIG. 2. A diode which is connected in series with the originally present substrate diode with opposite polarity is produced, in addition. In the equivalent circuit according to FIG. 2 the original substrate diode 10 is indicated as the substrate diode 101 with its depletion layer capacitance 91 and its series loss resistor 81. The series resistor 81 and capacitance 91 of the substrate diode 101 have remained approximately equal in magnitude as in the original substrate diode 10 by means of this change. The additional diode 102 connected in series with the diode 101 comprises the depletion layer capacitance 92 and the series resistor 82. It is made up of different partial diodes. The point in question is that its capacitance 92 be kept small relative to the substrate capacitance 91. The smaller the capacitance 92, the lower the losses in the substrate, but the more the substrate potential also corresponds to the collector potential relative to high frequency. The diode 102 is produced in that the highly doped p-type regions 14 (FIG. 5) which proceed from the upper main surface of a silicon layer, extend into the silicon and are connected to ground potential, are replaced by the n-doped regions 13, 15, 17 (FIG. 6). 
     If a shield grid which is insulated by means of oxide and connected to ground is located over the epitaxy, the equivalent wiring diagram shown in FIG. 3 is valid. The oxide capacitance 103, whose loss resistance relative to the resistors 81, 82 is negligible, is connected in series with the series connection of the substrate diode 101 and the diode 102. The same applies in an analogous manner to the lower main surface between substrate and heat sink. 
     In the frequency range from approximately 500 MHz to 1000 MHz, the different embodiment forms act chiefly by means of the series connection of the additional capacitances 92 or 92 and 103, respectively. 
     FIG. 4 shows a top view of a portion of a high-frequency transistor, of the invention, and FIGS. 5 and 6 show respectively the side section along section line AB. 
     As already mentioned, the contacts of emitter, base and collector are designated by reference numbers 2, 3, 4. Resistors 5 are introduced in the feed lines to the partial emitters as stabilization resistors, wherein connecting lines 21 extend from the resistors 5 to the emitters. Moreover, a metallic shield 20 is provided at the edge. 
     The p-doped substrate 11, the buried collector layer 12, the n-doped epitaxy 13 which is deposited on the latter, the diffused in insulation 14, the diffused in deep collector contact region 15, the base region 16 and the emitter region 17 can be seen in the sectional drawing (FIG. 5 and FIG. 6). 
     The p-n junctions occurring at the upper main surface are covered with the oxide layer 18 shown in this drawing with uniform thickness. The metallic contacts and connections, respectively, such as the emitter contact 2, connecting lines 21, base contact 3 and shield 20 are arranged on this oxide layer. Contacts to the diffusion regions located under the oxide layer are provided in corresponding oxide windows. Connection between the collector contacts 4 and the collector contact diffusion region (15) is established through windows 41 by means of metallizations indicated by hatched lines in FIG. 4. Similar metallizations serve as connection lines 21 for emitter contacts 2 and for base contacts 3. A metallization 22 on an isolating layer 19, which can be constructed as a dielectric layer or depletion layer, is located on the lower main surface of the substrate 11. 
     The substrate diode 10 of FIG. 1 is formed by the boundary layer of the collector space 12, 13 relative to the substrate 11. The capacitive back effect of the collector on the base contact 3 is drastically reduced by the open low-impedance diffusion 14 which is connected to ground via the connection line 20. The emitter resistors 5 can be produced with the emitter diffusion 17, the deep collector 15 and possibly also the buried layer 12 so as to be connected in parallel with the latter. 
     FIG. 6 shows a modification of the arrangement shown in FIG. 5. The large-area regions 14 of FIG. 5, which are connected with the grounded connections 2 and shield 20 and form an isolating diffusion, are omitted in the construction according to FIG. 6 and are substituted by the oppositely doped epitaxy 13 and the deep collector 15 with emitter 17, which is located partially above the latter. The substrate diode 10 has become the substantially similar substrate diode 101. There are now n-doped regions located between the metallic regions 2, 20 and the substrate 11, so that the additional diode 102 is formed. The latter is connected in series with the substrate diode 101 with opposite polarity so that the capacitive displacement current, and accordingly also the losses in the ohmic bulk regions, is smaller. A depletion layer formed between the metallization 22 connected with metal or with a heat sink, respectively, and the substrate 11 is likewise effective. This can be applied to the lower principle plane of the substrate 11 as a dielectric layer 19.