Abstract:
A Bi-CMOS logic circuit includes a Bi-CMOS circuit which is composed of first and second bipolar transistors, first and second resistors, and first and second MOS transistors. An input signal is applied to the gates of the first and second MOS transistors, and an output signal is drawn from a connection node at which the first and second bipolar transistors are connected in series between first and second power sources. A third MOS transistor is connected between the collector and emitter of the first bipolar transistor. The input signal is applied to the gate of the third MOS transistor. In place of or in addition to the third MOS transistor, a fourth MOS transistor is provided which is connected between the collector and emitter of the second bipolar transistor. The third and fourth MOS transistors function to decrease roundings of rising and falling edges of the waveform of the output signal.

Description:
BACKGROUND OF THE INVENTION 
     The present invention generally relates to a Bi-CMOS logic circuit, and more particularly to an improvement in the rise and fall characteristics of an output signal from the Bi-CMOS logic circuit. 
     As is well known, a Bi-CMOS logic circuit is composed of a bipolar element and a CMOS (complementary metal oxide semiconductor transistor) element. Referring to FIG.1, there is illustrated a conventional Bi-CMOS logic circuit, which includes a CMOS inverter composed of a P-channel MOS transistor MP1 and an N-channel MOS transistor MN1 and a pair of bipolar transistors Q1 and Q2. The Bi-CMOS logic circuit has a high operating speed characteristic afforded by the bipolar transistor pair and a low power consumption characteristic afformed by the CMOS inverter. A resistor R1 (impedance circuit) is connected between the base and emitter of the bipolar transistor Q1 and a resistor R2 (impedance circuit) is connected between the base and emitter of the bipolar transistor Q2. An output terminal OUT of the Bi-CMOS logic circuit is grounded through a wiring load capacitance C, which is a parasitic capacitance. 
     The bipolar transistors Q1 and Q2 are connected in series between a positive power source Vcc and a negative power source (ground). The output signal from the Bi-CMOS logic circuit is drawn from a connection node at which the emitter of the bipolar transistor Q1 is connected to the collector of the bipolar transistor Q2. The MOS transistor MP1 is connected between the collector and base of the bipolar transistor Q1. The MOS transistor MN1 is connected between the collector and base of the bipolar transistor Q2. An input signal applied to an input terminal IN is supplied to the gates of the MOS transistors MP1 and MN1. 
     When the input signal (also indicated by IN) changes from a high (H) level (approximately equal to the power source voltage Vcc) to a low level (approximately equal to the ground potential), the MOS transistor MP1 is switched from OFF to ON. In response to this change in the state of the MOS transistor MP1, the bipolar transistor Q1 is turned ON. Thus, the load capacitance C is charged so that the output signal (also indicated by OUT) at the output terminal OUT is changed from the low level to the high level. 
     During the time when the voltage of the output terminal OUT increases to a potential equal to Vcc-V BE  (base-emitter voltage of the bipolar transistor Q1), most of current passes through the bipolar transistor Q1. This is due to the fact that the current driveability of the bipolar transistor Q1 is greater than that of the MOS transistor MP1. The current passing through the bipolar transistor Q1 charges the load capacitance C. When the collector-emitter voltage of the bipolar transistor Q1 becomes equal to or greater than the base-emitter voltage V BE  thereof, the bipolar transistor Q1 cannot pass current. In this state, the load capacitance C is charged by a current passing through the MOS transistor MP1 and the resistor R1. Thereby, the voltage of the output terminal OUT gradually increases toward the power source voltage Vcc and finally becomes equal to the high level (approximately equal to Vcc). 
     On the other hand, when the input signal changes from the low level to the high level, the MOS transistor MP1 is switched from ON to OFF and the MOS transistor MN1 is switched from OFF to ON. In response to this change in the state of the MOS transistor MN1, the bipolar transistor Q2 is turned ON. Thus, the load capacitance C is discharged through the bipolar transistor Q2 so that the voltage of the output terminal OUT is changed from the high level to the low level. Until the time when the voltage of the output terminal OUT decreases to the base-emitter voltage V BE  of the bipolar transistor Q2, most of current passes through the bipolar transistor Q2. This is due to the fact that the current driveability of the bipolar transistor Q2 is greater than that of the MOS transistor MN1. When the collector-emitter voltage of the bipolar transistor Q2 becomes equal to or less than the base-emitter voltage V BE  thereof, the bipolar transistor cannot pass current. Thus, the load capacitance C is gradually discharged through the MOS transistor MN1 and the resistor R2 and finally becomes equal to the low level (approximately equal to the ground potential). 
     A description will now be given of the disadvantages of the above-mentioned conventional Bi-CMOS logic circuit with reference to FIG.2. FIG.2 is a waveform diagram of the output signal OUT obtained at the output terminal OUT. A letter &#34;a&#34; denotes the potential difference between the emitter and base of the bipolar transistor Q1, and a letter &#34;b&#34; denotes the potential difference between the emitter and base of the bipolar transistor Q2. A letter &#34;c&#34; denotes the time it takes the output voltage to increase by the potential difference &#34;a&#34;, and a letter &#34;d&#34; denotes the time it takes the output voltage to decrease by the potential difference &#34;b&#34;. 
     As shown in FIG.2, the signal waveform of the output signal OUT rises rapidly. After that, during the time &#34;c&#34;, the current passing through the resistor R1 charges the load capacitance C so that the voltage of the output terminal OUT increases gradually by the base-emitter voltage V BE  of the bipolar transistor Q1. The time when the current is passing through the load capacitance C is based on the time constant of R1 and C. Thus, it takes a long time for the output voltage to increase to the high level so that a rounding of the waveform of the output signal appears during the time &#34;c&#34;. Similarly, during the time &#34;d&#34;, the current from the load capacitance C passes through the resistor R2 so that the load capacitance is gradually discharged. Thus, a rounding of the falling waveform of the output signal appears during the time &#34;d&#34;. Thus, the period at which the output signal is maintained at the high level (approximately equal to Vcc) is short, which causes jitter, particularly when the Bi-CMOS logic circuit operates at high frequencies. 
     SUMMARY OF THE INVENTION 
     It is a general object of the present invention to provide an improved Bi-CMOS logic circuit in which the above-mentioned disadvantages are eliminated. 
     A more specific object of the present invention is to provide a Bi-CMOS logic circuit capable of providing decreased rounding of the output waveform and decreased jitter. 
     The above-mentioned objects of the present invention are achieved by a Bi-CMOS logic circuit comprising first and second bipolar transistors connected in series between a first power source and a second power source, an output signal being drawn from a connection node where the first and second bipolar transistors are connected in series; a first impedance circuit connected between a base and an emitter of the first bipolar transistor; and a second impedance circuit connected between a base of the second bipolar transistor and an emitter thereof. The Bi-CMOS logic circuit also comprises a first MOS transistor connected between a collector of the first bipolar transistor and the base thereof; and a second MOS transistor connected between a collector of the second bipolar transistor and the base thereof. An input signal is applied to gates of the first and second MOS transistors. The Bi-CMOS logic circuit further comprises a third MOS transistor connected between the collector of the first bipolar transistor and the emitter thereof. The input signal is applied to a gate of the third MOS transistor. It is also possible to provide a fourth MOS transistor in place of or in addition to the third MOS transistor. The fourth MOS transistor is connected between the collector and emitter of the second bipolar transistor. The input signal is applied to the gate of the fourth MOS transistor. 
     The aforementioned objects of the present invention are also achieved by a Bi-CMOS logic circuit comprising a NAND gate connected between a first power source and a second power source, the NAND gate having first and second input terminals and an output terminal, first and second input signals being applied to the first and second input terminals, respectively; a first MOS transistor connected between the first power source and the output terminal, the first input signal being applied to a gate of the first MOS transistor; a second MOS transistor connected between the first power source and the output signal, the second input signal being applied to a gate of the second MOS transistor; a third MOS transistor; and a fourth MOS transistor, the third and fourth MOS transistors being connected in series between the output signal and the second power source, the first and second input signals being applied to gates of the third and fourth MOS transistors, respectively. 
     The aforementioned objects of the present invention are also achieved by a Bi-CMOS logic circuit comprising a NOR gate connected between a first power source and a second power source, the NAND gate having first and second input terminals and an output terminal, first and second input signals being applied to the first and second input terminals, respectively; a first MOS transistor; a second MOS transistor, the first and second MOS transistors being connected in series between the first power source and the output terminal, the first and second input terminals being applied to gates of the first and second MOS transistors, respectively; a third MOS transistor connected in series between the output terminal and the second power source, the first input signal being applied to a gate of the third MOS transistor; and a fourth MOS transistor connected in series between the output terminal and the second power source, the second input signal being applied to a gate of the fourth MOS transistor. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     Other objects, features and advantages of the present invention will become apparent from the following detailed description when read in conjunction with the accompanying drawings, in which: 
     FIG.1 is a circuit diagram of a conventional Bi-CMOS logic circuit; 
     FIG.2 is a waveform diagram illustrating disadvantages of the conventional Bi-CMOS logic circuit shown in FIG.1; 
     FIG.3 is a circuit diagram of a Bi-CMOS logic circuit according to a first preferred embodiment of the present invention; 
     FIG.4 is a waveform diagram of an output signal from the Bi-CMOS logic circuit shown in FIG.3; 
     FIG.5 is a circuit diagram of a Bi-CMOS logic circuit according to a second preferred embodiment of the present invention; and 
     FIG.6 is a circuit diagram of a Bi-CMOS logic circuit according to a third preferred embodiment of the present invention. 
    
    
     DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     A description will now be given of a Bi-CMOS logic circuit according to the first preferred embodiment of the present invention with reference to FIG.3. In FIG.3, those parts which are the same as those shown in FIG.1 are given the same reference numerals. 
     According to the first embodiment of the present invention, P-channel MOS transistor MP2, related as a pair and N-channel MOS transistor MN2 are added to the configuration shown in FIG.1. The MOS transistor MP2 is connected between the collector and emitter of the bipolar transistor Q1. That is, the source and drain of the MOS transistor MP2 are connected to the collector and emitter, respectively, of the bipolar transistor Q1. Similarly, the MOS transistor MN2 is connected between the collector and emitter of the bipolar transistor Q2. That is, the drain and source of the MOS transistor MN2 are connected to the collector and emitter of the bipolar transistor Q2, respectively. The input signal IN through the input terminal IN is applied to the gates of the MOS transistors MP2 and MN2. 
     When the input signal changes from the high level to the low level, the MOS transistors MP1 and MP2 are switched from OFF to ON, and the MOS transistors MN1 and MN2 are switched from ON to OFF. In this change in the status of the MOS transistor MP1, the bipolar transistor Q1 is turned ON and charges the load capacitance C. Thus, the output voltage of the output terminal OUT is changed from the low level to the high level. During this operation, current from the power source Vcc passes through the bipolar transistor Q1 and charges the load capacitance C until the output voltage increases to the potential equal to Vcc-V BE  (base-emitter voltage of the bipolar transistor Q1). Thus, the output voltage rises rapidly. It will be noted that the current driveability of the bipolar transistor Q1 is greater than that of each of the MOS transistors MP1 and MP2. When the output voltage has become equal to Vcc-V BE , current starts to pass through the MOS transistor MP2 and charges the load capacitance C. It will be noted that the MOS transistor MP2 operates at a speed greater than that of the resistor R1. 
     On the other hand, when the input signal changes from the low level to the high level, the MOS transistors MP1 and MP2 are switched from ON to OFF, and the MOS transistors MN1 and MN2 are switched from OFF to ON. Since the MOS transistor MN1 is turned ON, the bipolar transistor Q2 is also turned ON. Thus the load capacitance C is discharged so that the output voltage of the output terminal OUT is changed from the high level to the low level. During the discharging operation, current from the load capacitance C passes through the bipolar transistor Q2 until the output voltage decreases to the base-emitter voltage V BE  of the bipolar transistor Q2. Thus, the output voltage decreases rapidly. It will be noted that the current driveability of the bipolar transistor Q2 is greater than that of each of the MOS transistors MN1 and MN2. When the output voltage has become equal to V BE  of the bipolar transistor Q2, current from the load capacitance C starts to pass through the MOS transistor MN2 so that the output voltage becomes approximately equal to the low level (approximately equal to the ground level). It will be noted that the MOS transistor MN2 operates at a speed greater than that of the resistor R2. 
     FIG.4 is a waveform diagram of the output signal obtained at the output terminal OUT shown in FIG.3. The letters &#34;a&#34;, &#34;b&#34;, &#34;c&#34; and &#34;d&#34; are as follows. Letter &#34;a&#34; denotes the potential difference between the emitter and base of the bipolar transistor Q1, and letter &#34;b&#34; denotes the potential difference between the emitter and base of the bipolar transistor Q2. Letter &#34;c&#34; denotes the time it takes the output voltage to increase by the potential difference &#34;a&#34;, and letter &#34;d&#34; denotes the time it takes the output voltage to decrease by the potential difference &#34;b&#34;. 
     During the time &#34;c&#34;, the current passes through the MOS transistor MP2 and charges the load capacitance C by the base-emitter voltage V BE  of the bipolar transistor Q1. Thus, it is possible to increase the output voltage to the high level (approximately equal to Vcc) during a reduced time, as compared with the aforementioned conventional circuit in which the load capacitance C is charged by the current which passes through the resistor R1. According to the configuration shown in FIG.3, it takes about 0.2 ns to increase the output signal to the high level. Thus, the rising waveform of the output signal has a reduced rounding, as shown in FIG.4. It will be noted that according to the aforementioned conventional circuit it takes about 1.6 ns to increase the output signal to the high level. 
     During the time &#34;d&#34;, current from the load capacitance C passes through the MOS transistor MN2. Thus, it becomes possible to decrease the output voltage to the low level (approximately equal to the ground potential) during a reduced time, as compared with the aforementioned conventional circuit in which the current from the load capacitance C passes through the resistor R2. Thus the falling waveform of the output signal has a reduced rounding, as shown in FIG.4. It should be particularly noted that the output signal can be maintained at the high level during a lengthened period of time. Thus, it is possible to suppress the occurrence of jitter. Thus, the circuit shown in FIG.3 can operate at higher frequencies. 
     When it is desired to eliminate only the rounding of the rising waveform, it is possible to provide only the MOS transistor MP2. That is, the MOS transistor MN2 may be omitted. On the other hand, when it is desired to eliminate only the rounding the falling waveform, it is possible to provide only the MOS transistor MN2. 
     A description will now be given of a Bi-CMOS logic circuit according to a second preferred embodiment of the present invention with reference to FIG.5. The Bi-CMOS logic circuit shown in FIG.5 is a two-input NAND gate. A conventional NAND gate 100 is made up of two bipolar transistors Q1 and Q2, two P-channel MOS transistors MP3 and MP4 and two N-channel MOS transistor MN3 and MN4. According to the second embodiment of the present invention, two P-channel MOS transistors MP5 and MP6 and two N-channel MOS transistors MN5 and MN6 are added to the conventional NAND gate 100. The source and drain of each of the MOS transistors MP5 and MP6 are connected to the collector and emitter, respectively, of the bipolar transistor Q1. An input signal IN1 is applied to the gate of the MOS transistor MP5, and an input signal IN2 is applied to the gate of the MOS transistor MP6. The MOS transistors MN5 and MN6 are connected in series between the collector and emitter of the bipolar transistor Q2. That is, the drain of the MOS transistor MN5 is connected to the collector of the bipolar transistor Q2, and the source thereof is connected to the drain of the MOS transistor MN6. The source of the MOS transistor MN6 is grounded. 
     Each of the MOS transistors MP3 and MP4 is connected between the collector and emitter of the bipolar transistor Q1. The input signals IN1 and IN2 are applied to the gates of the MOS transistors MP3 and MP4, respectively. The MOS transistors MN3 and MN4 are connected in series between the collector and base of the bipolar transistor Q2. The input signals IN1 and IN2 are applied to the gates of the MOS transistors MN3 and MN4, respectively. 
     It is now assumed that no charge is stored in the load capacitance C. In this state, when the input signal IN1 changes from the high level to the low level (while the input signal is maintained at the high level), the MOS transistor MP3 is switched from OFF to ON so that current passes through the bipolar transistor Q1 and charges the load capacitance C. The MOS transistor MP5 is also turned ON when the input signal IN1 changes from the high level to the low level. As the driveability of the bipolar transistor Q1 is greater than the driveability of the MOS transistor MP5, most of current from the power source Vcc passes through the bipolar transistor Q1. When the output voltage has become equal to Vcc-V BE  (base-emitter voltage of the bipolar transistor Q1), the bipolar transistor Q1 cannot pass current from the power source Vcc. Instead, the current from the power source Vcc passes through the MOS transistor MP5 and charges the load capacitance C. Thus, the output voltage is rapidly increased by the base-emitter voltage V BE  of the bipolar transistor Q1 so that the output signal becomes approximately equal to the power source voltage Vcc. 
     In this state, when the input signal IN1 changes from the low level to the high level (the input signal IN2 is maintained at the high level), the MOS transistors MN3 and MN5 are turned ON so that all the N-channel MOS transistors MN3-MN6 are ON. The current from the load capacitance C is allowed to pass through the bipolar transistor Q2 so that the output voltage rapidly decreases by Vcc-V BE  (the emitter-base voltage of the bipolar transistor Q2). After that, the bipolar transistor Q2 no longer passes any current. Instead, the current from the load capacitance C passes through the MOS transistors MN5 and MN6 so that the output voltage is rapidly decreased approximately to the ground potential. It will be noted that the current driveability of each of the MOS transistors MN5 and MN6 is greater than the resistor R2. 
     In the above-mentioned second embodiment of the present invention, it is also possible to provide either a pair of MOS transistors MP5 and MN5 or a pair of MOS transistors MP6 and MN6. 
     A description will now be given of a Bi-CMOS circuit according to a third preferred embodiment of the present invention with reference to FIG.6. The Bi-CMOS circuit shown in FIG.6 is a two-input NOR gate. A conventional NOR gate 200 is composed of two bipolar transistors Q1 and Q2, two P-channel MOS transistors MP7 and MP8 and two N-channel MOS transistors MN7 and MN8. According to the third embodiment of the present invention, two P-channel MOS transistors MP9 and MP10 and two N-channel MOS transistors MN9 and MN10 are added to the conventional NOR gate 200. The MOS transistors MP9 and MP10 are connected in series between the collector and emitter of the bipolar transistor Q1. That is, the source of the MOS transistor MP9 is connected to the collector of the bipolar transistor Q1, and the drain thereof is connected to the source of the MOS transistor MP10. The drain of the MOS transistor MP10 is connected to the emitter of the bipolar transistor Q1. The input signals IN1 and IN2 are applied to the gates of the MOS transistors MP9 and MP10, respectively. Each of the MOS transistors MN9 and MN10 are connected between the collector and emitter of the bipolar transistor Q2. The input signals IN1 and IN2 are applied to the gates of the MOS transistors MN9 and MN10, respectively. 
     The MOS transistors MP7 and MP8 are connected in series between the collector and base of the bipolar transistor Q1. Each of the MOS transistors MN7 and MN8 is connected between the collector and base of the bipolar transistor Q2. The input signals IN1 and IN2 are applied to the gates of the MOS transistors MN7 and MN8, respectively. 
     It is now assumed that the input signals IN1 and IN2 are at the high level and no charge is stored in the load capacitance C. When both the input signals IN1 and IN2 change from the high level to the low level, all the P-channel MOS transistors are ON, and all the N-channel MOS transistors are OFF. Current from the power source Vcc passes through the bipolar transistor Q1 and charges the load capacitance C. When the output voltage has become equal to Vcc-V BE  (base-emitter voltage of the bipolar transistor Q1), the bipolar transistor Q1 cannot pass current. After that, the current from the power source Vcc starts to pass through the MOS transistors MP9 and MP10 and charges the load capacitance C. Thus, the output voltage is increased to the high level rapidly. It will be noted that the current driveability of each of the MOS transistors MP9 and MP10 is greater than the resistor R1. 
     When the input signal IN1 changes from the low level to the high level while the input signal IN2 is maintained at the low level, the MOS transistors MP7 and MP9 are turned OFF and the MOS transistors MN7 and MN9 are turned ON. Current resulting form a charge stored in the load capacitance C passes through the bipolar transistor Q2 so that the output voltage decreases by Vcc-V Be  (base-emitter voltage of the bipolar transistor Q2). When the output voltage has become equal to Vcc-V BE , the bipolar transistor Q2 cannot pass current. After that, the current from the load capacitance C starts to pass through the MOS transistor MN9 so that the output voltage becomes equal to the low level rapidly. 
     In the above-mentioned third embodiment of the present invention, it is also possible to provide only a pair of MOS transistors MP9 and MN9 or a pair of MOS transistors MP10 and MN10. 
     The present invention is not limited to the specifically described embodiments, variations and modifications may be made without departing from the scope of the present invention.