Abstract:
An apparatus for effecting high speed switching of a communication signal between a first component and a second component includes: (a) a switching circuit configured for receiving the signal from the first component that includes a plurality of switch elements responding to the signal to produce an interim signal that is substantially a model of the signal; (b) a follower circuit having an input locus coupled with the switching circuit for receiving the interim signal; the follower circuit has an output locus configured for presenting an output signal that is substantially duplicating the interim signal; and (c) a control circuit coupling the follower circuit with the switching circuit and receives a feedback signal from the follower circuit representative of the output signal; the control circuit responds to the feedback signal to effect operation of the switching circuit to control at least one first parameter relating to the interim signal.

Description:
BACKGROUND OF THE INVENTION 
     The present invention is directed to communication signal driver apparatuses, and especially to communication signal driver apparatuses that handle high-speed signal traffic between components. 
     High speed chip-to-chip signaling is a significant bottleneck in the design of systems such as motherboards, optical transmission links, intelligent network hubs, routers and other systems. Some standards have been established to apply to high speed signal handling applications including, for example, low voltage differential signaling (LVDS) and positive emitter-coupled logic (PECL). These standards are designed to achieve high-speed signal handling with low power dissipation and low electromagnetic interference (EMI). 
     Inter-chip high-speed communication is limited by the performance of driver and receiver circuits at the interface of communicating chips. In particular, it is important for driver apparatuses to exhibit high-speed signal handling as well as low power dissipation while operating using low supply voltages. Other desirable attributes for a driver apparatus are scalability and variability of the apparatus for satisfying various standards to which driver apparatuses may be required to adhere. 
     SUMMARY OF THE INVENTION 
     In a communication system, the driver speed is not only limited by the external load that is driven, but also by the structure of the circuitry used to drive the external loads. In its preferred embodiment, the present invention is an apparatus, such as a driver circuit, for conveying a communication signal. The apparatus is preferably constructed to include a switching circuit, a follower circuit that follows the switching circuit and a control circuit. The control circuit provides a feedback signal from the follower circuit to the switching circuit to control at least one parameter associated with operation of the switching circuit. The switching circuit is preferably constructed as a differential switching stage with resistive loads. A bias current through the resistive loads establishes the required differential voltage at the output of the apparatus. The switching circuit also controls the common mode voltage at the output of the apparatus. The follower circuit translates the differential voltage generated by the switching circuit to the output of the apparatus. The control circuit senses the common mode voltage at the output of the apparatus and provides an amplified error signal to the switching circuit. 
     This arrangement provides for high-speed operation because of low output impedance of the follower circuit (i.e., the output stage of the apparatus) and because there is no switching effected in the output stage of the apparatus. Because the entire apparatus may be advantageously constructed with minimal stacking of devices and with low voltage drops within the circuitry, the apparatus is particularly well suited for low voltage applications. Further, since the output stage (i.e., the follower circuit) includes no switching devices, there is no requirement for large currents in the follower circuit for high speed operation. The preferred output stage (i.e., follower circuit) construction also facilitates either high or low output common-mode voltage operation. Circuit parameters and particular components in the apparatus may easily be varied to satisfy particular requirements for various standards including, for example, output differential voltage, speed, and power dissipation. 
     An apparatus for effecting high speed switching of a communication signal between a first component and a second component includes: (a) a switching circuit configured for receiving the communication signal from the first component; the switching circuit includes a plurality of switch elements responding to the communication signal to produce an interim signal that is substantially a model of the communication signal; (b) a follower circuit having an input locus coupled with the switching circuit for receiving the interim signal; the follower circuit has an output locus configured for presenting an output signal that is substantially duplicating the interim signal; and (c) a control circuit coupling the follower circuit with the switching circuit; the control circuit receives a feedback signal from the follower circuit that is representative of the output signal; the control circuit responds to the feedback signal to effect operation of the switching circuit to control at least one first parameter relating to the interim signal. 
     It is therefore an object of the present invention to provide an apparatus for conveying a signal that exhibits high-speed signal handling and low power dissipation. 
     It is a further object of the present invention to provide an apparatus for conveying a signal that can operate using low supply voltages. 
     It is yet a further object of the present invention to provide an apparatus for conveying a signal that exhibits scalability and variability for satisfying various standards. 
    
    
     Further objects and features of the present invention will be apparent from the following specification and claims when considered in connection with the accompanying drawings, in which like elements are labeled using like reference numerals in the various figures, illustrating the preferred embodiments of the invention. 
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is an electrical schematic diagram of a first embodiment of a prior art communication switching apparatus. 
     FIG. 2 is an electrical schematic diagram of a second embodiment of a prior art communication switching apparatus. 
     FIG. 3 is an electrical schematic diagram of a third embodiment of a prior art communication switching apparatus. 
     FIG. 4 is an electrical schematic diagram of a communication switching apparatus configured according to the present invention. 
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT 
     In a typical communication system a driver apparatus is commonly part of a transmitter block, or component. The driver apparatus is the interface to the transmission media by which the communication signals are conveyed. It is the driver apparatuses in a system that usually limit the data rates that can be handled by a system operating according to a given standard because of inherent limitations in the driver apparatuses. Conventional driver apparatus designs have so far been able to meet the demands of ever increasing data rate requirements, but driver apparatus designs now in use are bothersome bottlenecks for even faster data rates of signal transmission. 
     FIG. 1 is an electrical schematic diagram of a first embodiment of a prior art communication switching apparatus. In FIG. 1, a driver apparatus  10  includes a switching circuit  12  and a control circuit  14 . Switching circuit  12  includes first input loci  20 ,  22 . The signal conveyed by driver apparatus  10  is a differential signal so that the positive component VIN+ of the input signal is received at first input locus  20 , and the negative component VIN− of the input signal is received at first input locus  22 . First input loci  20 ,  22  are coupled with gates  24 ,  26  of switching transistors Q 1 , Q 2 . Drains  28 ,  30  of switching transistors Q 1 , Q 2  are coupled with a current source  32 . Current source  32  is coupled to receive supply voltage Vcc. Resistors R 1 , R 2  are coupled in series across sources  34 ,  36  of switching transistors Q 1 , Q 2 . 
     Switching circuit  12  further includes second input loci  40 ,  42 . The positive component VIN+ of the differential input signal is received at second input locus  42 , and the negative component VIN− of the differential input signal is received at second input locus  40 . Second input loci  40 ,  42  are coupled with gates  44 ,  46  of switching transistors Q 3 , Q 4 . Drain  48  of switching transistor Q 3  is coupled with source  34  of switching transistor Q 1 . Drain  50  of switching transistor Q 4  is coupled with source  36  of switching transistor Q 2 . Thus resistors R 1 , R 2  are also coupled in series across drains  48 ,  50  of switching transistors Q 3 , Q 4 . Sources  54 ,  56  are coupled with a current source  58 . Current source  58  is coupled with ground  60 . A load resistor R LOAD  and a load capacitor C LOAD  are coupled in parallel across sources  34 ,  36  of switching transistors Q 1 , Q 2  and across drains  48 ,  50  of switching transistors Q 3 , Q 4 . 
     Output loci  62 ,  64  are coupled from adjacent opposite ends of load resistor R LOAD . Positive component VOUT+ of the differential output signal is presented at output locus  62 . Negative component VOUT− of the differential output signal is presented at output locus  64 . 
     A feedback line  70  is coupled with a juncture  68  between resistors R 1 , R 2 . Feedback line  70  is coupled with an amplifier  72  in control circuit  14 . Amplifier  72  also receives a reference voltage V REF . Amplifier  72  presents an amplified error signal at a line  74  representing the difference between a signal appearing on feedback line  70  and reference voltage V REF . Line  74  is coupled with current source  32 . Amplified error signals on line  74  are employed to effect control of current source  32 , thereby controlling current through switching transistors Q 1 , Q 2 , Q 3 , Q 4 . 
     In apparatus  10  switching transistors Q 1 , Q 2 , Q 3 , Q 4  act as switches in a manner whereby either switching transistors Q 1 , Q 4  or switching transistors Q 2 , Q 3  provide a path for current flow to generate the required differential voltage across load resistor R LOAD . In essence, switching transistors Q 1 , Q 2 , Q 3 , Q 4  operate in the manner of an H-bridge network. Resistors R 1 , R 2  are used to sense the common-mode voltages at output loci  62 ,  64  for provision via feedback line  70  to amplifier  72 . Amplified error signals on line  74  generated by amplifier  72  control current source  32  in order to effect control of the output common mode voltage measured at output loci  62 ,  64 . 
     A significant disadvantage with the architecture of apparatus  10  is that switching transistors Q 1 , Q 2 , Q 3 , Q 4  increase the voltage rise and fall time at output loci  62 ,  64 , which in turn affects the data rate of apparatus  10 . Voltage rise and fall times of switching transistors Q 1 , Q 2 , Q 3 , Q 4 , are greater when sources  34 ,  36 ,  54 ,  56  or drains  28 ,  30 ,  48 ,  50  see large resistances or capacitances. In most applications in which apparatus  10  is employed, even though load resistance may be small, load capacitance will typically be quite large, often on the order of at least 1 pF (picoFarad). One partial solution to these shortcomings of apparatus  10  could be to increase bias currents through switching transistors Q 1 , Q 2 , Q 3 , Q 4  (e.g., by reducing load resistor R LOAD ) to increase switching speed for switching transistors Q 1 , Q 2 , Q 3 , Q 4 . However, such a remedy would require large increments in power dissipation. Power dissipation would increase because of the increase in bias currents as well as because the larger bias currents would require larger switching transistors Q 1 , Q 2 , Q 3 , Q 4 . Larger switching transistors Q 1 , Q 2 , Q 3 , Q 4  mean that circuitry driving apparatus  10  inherently would dissipate more power than if the transistors were smaller. 
     In today&#39;s market the trend in products is toward lower supply voltages in order to create smaller, less battery-hungry devices. Apparatus  10  suffers from yet a further disadvantage in that it will operate more slowly for lower power supply voltages. This is a serious disadvantage in today&#39;s marketplace. 
     FIG. 2 is an electrical schematic diagram of a second embodiment of a prior art communication switching apparatus. In FIG. 2, a driver apparatus  110  includes a switching circuit  112  and a control circuit  114 . Switching circuit  112  includes input loci  120 ,  122 . The signal conveyed by driver apparatus  110  is a differential signal so that the positive component VIN+ of the input signal is received at input locus  120 , and the negative component VIN− of the input signal is received at input locus  122 . Input loci  120 ,  122  are coupled with gates  124 ,  126  of switching transistors Q 11 , Q 12 . Drain  128  of switching transistor Q 11  is coupled with a current source  132 . Drain  130  of switching transistor Q 12  is coupled with a current source  133 . Current sources  132 ,  133  are coupled to receive supply voltage Vcc. Resistors R 11 , R 12  are coupled in series across sources  134 ,  136  of switching transistors Q 11 , Q 12 . Sources  134 ,  136  are coupled with a current source  158 . Current source  158  is coupled with ground  160 . 
     A load resistor R LOAD  and a load capacitor C LOAD  are coupled in parallel across drains  128 ,  130  of switching transistors Q 11 , Q 12 . Output loci  162 ,  164  are coupled from adjacent opposite ends of load resistor R LOAD . Positive component VOUT+ of the differential output signal is presented at output locus  162 . Negative component VOUT− of the differential output signal is presented at output locus  164 . 
     A feedback line  170  is coupled with a juncture  168  between resistors R 11 , R 12 . Feedback line  170  is coupled with an amplifier  172  in control circuit  114 . Amplifier  172  also receives a reference voltage V REF . Amplifier  172  presents an amplified error signal at a line  174  representing the difference between a signal appearing on feedback line  170  and reference voltage V REF . Line  174  is coupled with control lines  175 ,  177  for controlling current sources  132 ,  133 . Amplified error signals on lines  174 ,  175 ,  177  are employed to effect control of current sources  132 ,  133  thereby controlling current through switching transistors Q 11 , Q 12 . 
     In apparatus  110  switching transistors Q 11 , Q 12  switch on alternately and therefore alternately provide a path for current flow to generate the required differential voltage across load resistor R LOAD . Resistors R 11 , R 12  are used to sense the common-mode voltages at output loci  162 ,  164  for provision via feedback line  170  to amplifier  172 . Error signals on lines  174 ,  175 ,  177  generated by amplifier  172  control current sources  132 ,  133  in order to effect control of the output common mode voltage measured at output loci  162 ,  164 . 
     Apparatus  110  suffers from disadvantages similar to the disadvantages described in connection with apparatus  10  (FIG.  1 ). Because of the high impedance seen at the output of apparatus  110 , there are long rise and fall times, thereby limiting data rates that can be handled by apparatus  110 . Apparatus  110  is improved over apparatus  10  (FIG. 1) in that apparatus  110  operates at higher speeds for lower supply voltages. 
     FIG. 3 is an electrical schematic diagram of a third embodiment of a prior art communication switching apparatus. In FIG. 3, a driver apparatus  210  specifically suited for operation under the PECL (positive emitter-coupled logic) standard includes a switching circuit  212  and an output circuit  215 . Switching circuit  212  includes input loci  220 ,  222 . The signal conveyed by driver apparatus  210  is a differential signal so that the positive component VIN+ of the input signal is received at input locus  220 , and the negative component VIN− of the input signal is received at input locus  222 . Input loci  220 ,  222  are coupled with bases  224 ,  226  of switching transistors Q 21 , Q 22 . Collector  228  of switching transistor Q 21  is coupled with a resistor R 23  in series with a supply voltage Vcc. Collector  230  of switching transistor Q 22  is coupled with a resistor R 24  in series with a supply voltage Vcc. Resistors R 23 , R 24  limit current spikes when switching transistors Q 21 , Q 22  switch on and off. Emitters  234 ,  236  of switching transistors Q 21 , Q 22  are coupled with a current source  258 . Current source  258  is coupled with ground  260 . 
     Indicator signals indicating whether a respective switching transistor Q 21 , Q 22  is on or off are conveyed via lines  223 ,  225  to output circuit  215 . Output circuit  215  includes follower transistors Q 23 , Q 24 . Collector  248  of follower transistor Q 23  is coupled for receiving supply voltage Vcc. Collector  250  of follower transistor Q 24  is coupled for receiving supply voltage Vcc. Emitter  254  of follower transistor Q 23  is coupled with a resistor R 21  in series with a DC voltage source  266  and ground  268 . Emitter  256  of follower transistor Q 24  is coupled with a resistor R 22  in series with DC voltage source  266  and ground  268 . 
     Output locus  264  is coupled with emitter  254  of follower transistor Q 23 . Output locus  262  is coupled with emitter  256  of follower transistor Q 24 . Positive component VOUT+ of the differential output signal is presented at output locus  262 . Negative component VOUT− of the differential output signal is presented at output locus  264 . Since base  244  of follower transistor Q 23  is coupled with line  223  and base  246  of follower transistor Q 24  is coupled with line  225 , follower transistors Q 23 , Q 24  are controlled by signals appearing on lines  223 ,  225 . Recall that signals appearing on lines  223 ,  225  represent whether switching transistors Q 21 , Q 22  are on or off. As a result, output circuit  215  follows switching circuit  212  in operating follower transistors Q 23 , Q 24 . No control circuitry is provided for apparatus  210 . There is no on-chip locus available for determining the common mode voltage of the output from apparatus  210 . 
     Apparatus  210  is an example of a driver apparatus that is specifically designed for use with the PECL standard. Accordingly, the appropriate load resistor and load capacitor are not resident on-chip in apparatus  210 . Appropriate load resistance and load capacitance must be provided off-chip when using apparatus  210  to establish the circuit parameters required by the PECL standard, such as impedance value of the load resistance, current flow through the load and other parameters. Apparatus  210  operates at higher data rates than apparatus  10  (FIG. 1) and apparatus  110  (FIG.  2 ). 
     FIG. 4 is an electrical schematic diagram of a communication switching apparatus configured according to the present invention. In FIG. 4, a driver apparatus  310  includes a switching circuit  312 , a follower circuit  315  and a control circuit  314 . Switching circuit  312  includes input loci  320 ,  322 . The signal conveyed by driver apparatus  310  is a differential signal so that the positive component VIN+ of the input signal is received at input locus  320 , and the negative component VIN− of the input signal is received at input locus  322 . Input loci  320 ,  322  are coupled with bases  324 ,  326  of switching transistors Q 31 , Q 32 . Collector  328  of switching transistor Q 31  is coupled with a resistor R 33  in series with control circuit  314 . Collector  330  of switching transistor Q 32  is coupled with a resistor R 34  in series with control circuit  314 . Emitter  334  of switching transistor Q 31  is coupled with a resistor R 31  in series with a current source  358  and ground  360 . Emitter  336  of switching transistor Q 32  is coupled with a resistor R 32  in series with a current source  358  and ground  360 . Resistors R 31 , R 32  limit current spikes when switching transistors Q 31 , Q 32  switch on and off. 
     Indicator signals indicating whether a respective switching transistor Q 31 , Q 32  is on or off are conveyed via lines  323 ,  325  to output circuit  315 . Output circuit  315  includes follower transistors Q 34 , Q 35 . Collector  348  of follower transistor Q 34  is coupled for receiving supply voltage Vcc. Collector  350  of follower transistor Q 35  is coupled for receiving supply voltage Vcc. Emitter  354  of follower transistor Q 34  is coupled with a current source  380 . Current source  380  is coupled with ground  382 . Emitter  356  of follower transistor Q 35  is coupled with a current source  384 . Current source  384  is coupled with ground  386 . Current sources  380 ,  384  are conveniently situated in apparatus  310  to independently control speed of operation (i.e., switching speed) of follower transistors Q 34 , Q 35  independent of the value of R LOAD . Further, increasing current supplied by current sources  380 ,  384  to increase switching speed of follower transistors Q 34 , Q 35  does not significantly contribute to power dissipation by apparatus  310 . 
     A load resistor R LOAD  and a load capacitor C LOAD  are coupled in parallel across emitters  354 ,  356  of follower transistors Q 34 , Q 35 . Output loci  360 ,  362  are coupled at either end of load resistor R LOAD . Positive component VOUT+ of the differential output signal is presented at output locus  362 . Negative component VOUT− of the differential output signal is presented at output locus  360 . Since base  344  of follower transistor Q 34  is coupled with line  323  and base  346  of follower transistor Q 35  is coupled with line  325 , follower transistors Q 34 , Q 35  are controlled by signals appearing on lines  323 ,  325 . Recall that signals appearing on lines  323 ,  325  represent whether switching transistors Q 31 , Q 32  are on or off. As a result, output circuit  315  follows switching circuit  312  in operating follower transistors Q 34 , Q 35 . 
     Control circuit  314  operates to control common mode voltage of the output of apparatus  310 . Control circuit  314  includes resistors R 36 , R 37  coupled in series across emitters  354 ,  356  of follower transistors Q 34 , Q 35 . A feedback line  370  is coupled with a juncture  368  between resistors R 36 , R 37 . Feedback line  370  is coupled with an amplifier  372  in control circuit  314 . Amplifier  372  also receives a reference voltage V REF . Amplifier  372  presents an amplified error signal at an output line  374  representing the difference between a signal appearing on feedback line  370  and reference voltage V REF . Line  374  is coupled with gate  390  of switching transistor Q 33 . Source  392  of switching transistor Q 33  is coupled to receive supply voltage Vcc. Drain  394  of switching transistor Q 33  is coupled with a bypass capacitor C 31  and thence to ground  376 . Drain  394  of switching transistor Q 33  is also coupled with resistors R 33 , R 34 . Preferably apparatus  310  is configured so that node  333  acts as a virtual ground because capacitor C 1  is large enough to cause such a result. 
     Amplified error signals on line  374  are employed to gatingly control application of supply voltage Vcc to switching transistors Q 31 , Q 32 . That gating action affects signals appearing on lines  323 ,  325  which in turn affects operation of follower transistors Q 34 , Q 35 . When properly selected, transistor Q 33  may operate effectively as an adjustable resistor to determine common mode voltage at output loci  360 ,  362 . In such manner, amplified error signals on line  374  effect control of common mode voltage appearing at output loci  360 ,  362 . 
     Apparatus  310  overcomes the limitations of prior art driver apparatuses and the need for having either high or low common mode output voltages. Apparatus  310 , for the same power dissipation, generates significantly lower rise and fall times than apparatus  10  (FIG. 1) and apparatus  110  (FIG.  2 ). Apparatus  310  has three blocks, or circuits: a switching block, a follower block and a control block. In switching block  312  input signals received at input loci  320 ,  322  switch current between switching transistors Q 31 , Q 32 . Resistors R 31 , R 32  are used as degenerators to limit bias current spikes when switching transistors Q 31 , Q 32  are switched on and off. The differential voltage output from switching circuit  312  is provided to output circuit  315  on lines  323 ,  325 . Output circuit  315  operates as a follower stage. 
     The resistive impedance seen at nodes  329 ,  331  (at the ends of lines  323 ,  325  distal from follower transistors Q 34 , Q 35 ) can be adjusted to any small values. The capacitance seen at nodes  329 ,  331  comes from effective capacitance of C be  (base-to-emitter capacitance) for a respective follower transistor Q 34 , Q 35  coupled with C LOAD  and any parasitic capacitances. Thus, the effective capacitance seen at nodes  329 ,  331  is smaller than C LOAD  by a factor depending upon the relative values of C be , C LOAD  and β (current gain of the respective bipolar follower transistor Q 34 , Q 35 ). 
     The low resistances and capacitances seen at nodes  329 ,  331  result in faster rise and fall times and hence higher data rates for apparatus  310 . Another advantage of apparatus  310  is the facility with which apparatus  310  can be programmed or reconfigured to accommodate various parameters, such as parameters for conforming to predetermined standards, with little change in the design or topology of apparatus  310 . For example, simply by changing values for resistors R 33 , R 34  any differential voltage can be obtained at output loci  360 ,  362  for conforming to a standard. Other parameters important to standard adherence are also easily changed. 
     It is to be understood that, while the detailed drawings and specific examples given describe preferred embodiments of the invention, they are for the purpose of illustration only, that the apparatus and method of the invention are not limited to the precise details and conditions disclosed and that various changes may be made therein without departing from the spirit of the invention which is defined by the following claims.