Abstract:
Slow speed operation of a brushless DC (BLDC) motor is enhanced by gating off some of the PWM pulses in each commutation period. By doing so, longer PWM pulse widths may be used at PWM signal frequencies that are inaudible while still allowing desired slow speed operation of the BLDC motor. Centering the non-gated PWM pulses in each commutation period where peak back EMF occurs, further reduces losses and improves delivery of maximum torque from the BLDC motor.

Description:
RELATED PATENT APPLICATION 
       [0001]    This application claims priority to commonly owned U.S. Provisional Patent Application Ser. No. 61/249,745; filed Oct. 8, 2009; entitled “Slow Speed Operation of Brushless Direct Current Motors by Gating Pulse Width Modulation Drive,” by Ward R. Brown; and is related to commonly owned U.S. patent application Ser. No. ______; filed ______, 2010; entitled “Variable Pulse Width Modulation for Reduced Zero-Crossing Granularity in Sensorless Brushless Direct Current Motors,” by Ward R. Brown; and U.S. patent application Ser. No. ______; filed ______, 2010; entitled “Synchronized Minimum Frequency Pulse Width Modulation Drive for Sensorless Brushless Direct Current Motor,” by Ward R. Brown; wherein all are hereby incorporated by reference herein for all purposes. 
     
    
     TECHNICAL FIELD 
       [0002]    The present disclosure relates to brushless direct current (BLDC) motors, and more particularly, to slow speed operation of BLDC motors by gating pulse width modulation (PWM) drive. 
       BACKGROUND 
       [0003]    Brushless direct current (BLDC) motors are used in industries such as appliances, automotive, aerospace, consumer, medical, industrial automation equipment and instrumentation. BLDC motors do not use brushes for commutation, instead, electronic commutation is used. BLDC motors have advantages over brushed DC motors and induction motors such as: better speed versus torque characteristics, high dynamic response, high efficiency, long operating life, longer time intervals between service, substantially noiseless operation, and higher speed ranges. More detailed information on BLDC motors may be found in Microchip Application Notes: AN857, entitled “Brushless DC Motor Control Made Easy,” (2002); AN885, entitled “Brushless DC (BLDC) Motor Fundamentals,” (2003); AN894, entitled “Motor Control Sensor Feedback Circuits,” (2003); AN901, entitled “Using the dsPIC30 F for Sensorless BLDC Control,” (2004); and AN970, entitled “Using the PIC18F2431 for Sensorless BLDC Motor Control,” (2005); all are hereby incorporated by reference herein for all purposes. 
         [0004]    A three-phase BLDC motor completes an electrical cycle, i.e., 360 electrical degrees of rotation, in six steps at 60 electrical degrees per step. Synchronously at every 60 electrical degrees, phase current switching is updated (commutation). However, one electrical cycle may not correspond to one mechanical revolution (360 mechanical degrees) of the motor rotor. The number of electrical cycles to be repeated to complete one mechanical revolution depends upon the number of rotor pole pairs. For example, a four-pole BLDC motor will require two electrical cycles to complete one mechanical revolution of the motor rotor (see  FIG. 5 ). 
         [0005]    Drive commutation for a BLDC motor may be determined by position sensors that monitor the rotational position of the motor rotor shaft. Such position sensors may be, for example but are not limited to, Hall Effect position sensors embedded into the stator on the non-driving end of the motor. 
         [0006]    Drive commutation for a sensorless BLDC motor may also be determined by monitoring the back electromotive force (EMF) voltages at each phase (A-B-C) of the motor. The drive commutation is synchronized with the motor when the back EMF of the un-driven phase crosses one-half of the motor supply voltage during a commutation period. This is referred to as “zero-crossing” where the back EMF is equal to one-half of the motor supply voltage, over each electrical cycle. Zero-crossing is detected on the un-driven phase when the drive voltage is being applied to the driven phases. A voltage polarity change about the zero-crossing voltage of the back EMF on the un-driven phase may also be used in detecting a zero-crossing event, e.g., from positive to negative or negative to positive during application of the drive voltage to the driven phases within certain limits. 
         [0007]    The rotational speed of a BLDC motor is dependent upon the amplitude of the average DC voltages applied to the stator windings of the motor. The higher the average DC voltage applied the faster will the BLDC motor rotate. Generally, DC voltages are generated using pulse width modulation (PWM) to control the voltage amplitudes applied to the stator windings. The PWM maximum frequency is limited by the switching losses of the drive transistors. The PWM minimum frequency is limited by the undesirable audio emissions at frequencies in the audio range. An acceptable compromise is in the 15 KHz to 20 KHz range. PWM duty cycle can only be reduced to the point where the drive pulse width can still propagate through the drive power field effect transistors (FETs) and low-pass filter characteristics inherent in all motor designs. Reducing the PWM frequency would allow longer drive periods but this would also introduce audible noise from the motor. 
       SUMMARY 
       [0008]    The aforementioned problem is solved, and other and further benefits achieved by driving the brushless DC motor during a partial commutation period. The average drive voltage to the motor can be reduced further than available from the minimum pulse width and still maintain an inaudible PWM frequency by reducing the number of pulses in each commutation period. Therefore, average drive voltage to a BLDC motor can be further reduced by limiting the number of PWM pulses in each commutation period while maintaining an inaudible PWM signal period and duty cycle. 
         [0009]    According to a specific example embodiment of this disclosure, a method for controlling low speed operation of a brushless direct current motor comprises the steps of: generating a plurality of pulse width modulation (PWM) pulses at a certain duty cycle; determining electrical timing centers for each of a plurality of commutation periods of a brushless direct current motor; gating off some of the plurality of PWM pulses in each of the plurality of commutation periods, wherein the plurality of PWM pulses not gated off are grouped toward the electrical timing centers of the plurality of commutation periods; and driving power switching transistors with the plurality of PWM pulses not gated off during the plurality of commutation periods, wherein the power switching transistors are connected between the stator coils of the brushless direct current motor and a direct current power source. 
         [0010]    According to another specific example embodiment of this disclosure, a method for controlling low speed operation of a sensorless brushless direct current motor, said method comprising the steps of: generating a plurality of pulse width modulation (PWM) pulses at a certain duty cycle; determining electrical timing centers for each of a plurality of commutation periods of a brushless direct current motor by measuring back electromotive force voltages at each stator coil of the sensorless brushless direct current motor, and determining from the measured back electromotive force voltages when each of the measured back electromotive force voltages is at substantially a zero-crossing voltage value, wherein the zero-crossing voltage value is about one-half of a voltage value of a direct current power source; gating off some of the plurality of PWM pulses in each of the plurality of commutation periods, wherein the plurality of PWM pulses not gated off are grouped toward the electrical timing centers of the plurality commutation periods; and driving power switching transistors with the plurality of PWM pulses not gated off during the plurality commutation periods, wherein the power switching transistors are connected between the stator coils of the sensorless brushless direct current motor and the direct current power source. 
     
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         [0011]    A more complete understanding of the present disclosure thereof may be acquired by referring to the following description taken in conjunction with the accompanying drawings wherein: 
           [0012]      FIG. 1  illustrates a schematic diagram of a three-phase brushless direct current motor, Hall Effect position sensors and electronically commutating motor controller, according to a specific example embodiment of this disclosure; 
           [0013]      FIG. 2  illustrates a schematic diagram of a three-phase sensorless brushless direct current motor and electronically commutating motor controller, according to another specific example embodiment of this disclosure; 
           [0014]      FIG. 3  illustrates schematic diagrams showing current flows in each of the three stator windings of a three-phase brushless direct current motor during each 60 degree commutation period; 
           [0015]      FIG. 4  illustrates a more detailed schematic diagram of the back EMF zero-cross detectors shown in  FIG. 2 ; 
           [0016]      FIG. 5  illustrates schematic timing and amplitude graphs of a four-pole motor showing back electromotive force (EMF) voltages at each of the three stator windings during each 60 degree commutation period; and 
           [0017]      FIG. 6  illustrates schematic amplitude and timing graphs of voltages at one phase of the BLDC motor during each commutation period for different PWM duty cycles, according to the teachings of this disclosure. 
       
    
    
       [0018]    While the present disclosure is susceptible to various modifications and alternative forms, specific example embodiments thereof have been shown in the drawings and are herein described in detail. It should be understood, however, that the description herein of specific example embodiments is not intended to limit the disclosure to the particular forms disclosed herein, but on the contrary, this disclosure is to cover all modifications and equivalents as defined by the appended claims. 
       DETAILED DESCRIPTION 
       [0019]    Referring now to the drawing, the details of specific example embodiments are schematically illustrated. Like elements in the drawings will be represented by like numbers, and similar elements will be represented by like numbers with a different lower case letter suffix. 
         [0020]    Referring to  FIG. 1 , depicted is a schematic diagram of a three-phase brushless direct current motor, Hall Effect position sensors and electronically commutating motor controller, according to a specific example embodiment of this disclosure. A three-phase brushless direct current motor, generally represented by the numeral  100 , comprises a plurality of stator coils  102  and a rotor (not shown) having magnets arranged in a three-phase configuration. For discussion purposes the motor  100  described herein will be in a two pole three-phase configuration requiring 360 degrees of electrical rotation to produce one mechanical revolution of 360 degrees. The motor  100  is electronically commutated with power switching transistors  108  and  110  connected to the three-phase brushless direct current motor  100  and a direct current (DC) power source. The Hall Effect position sensors  104  supply rotor position information to a digital device  106  that may comprise a microcontroller (not shown), PWM generators having outputs coupled to power transistor drivers providing pulse width modulation (PWM) control outputs (PWM 0 -PWM 5 ) that are used to control turn-on and turn-off of the power switching transistors  108  and  110 . Based upon the combination of the three signals from the Hall Effect sensors  104 , the exact sequence of commutation can be determined. Use of Hall Effect position sensors  104  for rotor position indication is preferable and may even be required in low speed motor applications. 
         [0021]    The motor  100  is electronically commutated from a direct current (DC) source (not shown) through the power switching power transistors  108  and  110 , e.g., power field effect transistors (one pair per phase for a three-phase motor). The power transistors  108  and  110  are controlled by the digital device  106 , e.g., a microcontroller, that is coupled to the power transistors  108  and  110  through drivers for the power transistors (not shown). The digital device  106  provides six pulse width modulation (PWM) outputs, PWM 0 -PWM 5 , that control both the motor rotation direction and speed by turning on and off selected phase pairs of the power transistors  108  and  110  according to PWM signals appropriately sequenced and timed. 
         [0022]    Referring to  FIG. 2 , depicted is a schematic diagram of a three-phase sensorless brushless direct current motor and electronically commutating motor controller, according to another specific example embodiment of this disclosure. A three-phase sensorless brushless direct current motor, generally represented by the numeral  200 , comprises a plurality of stator coils  102  and a rotor (not shown) having magnets arranged in a three-phase configuration. For discussion purposes the motor  200  described herein will be in a two pole three-phase configuration requiring 360 degrees of electrical rotation to produce one mechanical revolution of 360 degrees. The motor  200  is electronically commutated with power switching transistors  108  and  110  connected to the three-phase sensorless brushless direct current motor  200  and a direct current (DC) power source. Back electromotive force (EMF) zero-cross detectors  204 , a digital device  206 , e.g., a microcontroller, having PWM generators that provide pulse width modulation (PWM) outputs coupled to power transistor drivers. The power transistor drivers (PWM 0 -PWM 5 ) control turn-on and turn-off of the power switching transistors  108  and  110 . 
         [0023]    Each stator coil  102  is connected to the positive of the DC power source for two commutation periods, the negative of the DC power source for two commutation periods, and is disconnected from both the positive and negative of the DC power source for two commutation periods. The motor phase position is determined by back electromotive force (EMF) voltages measured at a stator coil  102  when not connected to the DC power source at the time of measurement while the other two stator coils  102  are connected to the DC power source. The back EMF voltages at each of the stator coils  102  are monitored by the back EMF zero-cross detectors  204  (one per phase). However, the back EMF voltage to be measured requires connection to the positive of the DC power source of one of the stator coils  102  so as to enable current flow therethrough, thereby biasing the motor generated voltage to a level centered around the detection reference level (“zero-crossing” event), e.g., one-half the supply voltage. The other stator coil  102  of the pair of coils having current flow therethrough is connected to the negative of the DC power source. 
         [0024]    Referring to  FIG. 3 , depicted are schematic diagrams showing current flows in each of the three stator windings (coils  102 ) of a three-phase brushless direct current motor during each 60 degree commutation period. Rotation of the motor  100  is divided into six commutation periods (1) through (6), and current flows through different combinations of two of the three coils  102  during each of the six commutation periods. While combinations of two of the coils  102  are connected to the DC power source, a third coil  102  (three-phase motor) is not connected to the power source. However the unconnected coil  102  is monitored by the back EMF zero-cross detectors  204  such that upon detection of a “zero crossing” event, i.e., back EMF voltage on the unconnected coil  102  changes polarity while going through a substantially zero voltage (“zero voltage” is defined herein as one-half of the DC supply voltage). At approximately the zero voltage point detected by a respective one of the back EMF zero-cross detectors  204 , a synchronization relationship of the motor  200  stator coils  102  is ascertained, as more fully described hereinbelow. When Hall Effect position sensors  104  are used, back EMF zero-cross detection is not necessary as the Hall Effect position sensors  104  directly transmit the rotor position to the digital device  106 . 
         [0025]    Referring to  FIG. 4 , depicted is a more detailed schematic block diagram of the back EMF zero-cross detectors shown in  FIG. 2 . The back EMF zero-cross detectors  204  may comprise three-phase voltage divider resistors  418  and  420 , phase low-pass filters  422 , reference low-pass filter  430 , reference voltage divider resistors  426  and  428 , and voltage comparators  424 . The reference voltage divider resistors  426  and  428  are used to derive a “virtual” neutral reference voltage for use by the comparators  424  and/or the digital device  206  having analog inputs. The three-phase voltage divider resistors  418  and  420  reduce the stator coils  102  voltages to much lower voltages for use by the low-pass filters  422  and comparators  424 . Preferred resistance relationships for the resistors  418 ,  420 ,  426  and  428  are as follows: 
         [0000]      Raa=Rbb=Rcc=Rrr 
         [0000]        Ra=Rb=Rc= 2 *Rr    
         [0000]        Ra /( Raa+Ra )=Vcomparator_maximum_input/DC+)−(DC−))
 
         [0026]    The low pass filters  422  may be used to substantially reduce unwanted noise from the inputs to the comparators  424 . The comparators  424  are used in determining when a back EMF voltage on an unconnected coil  102  is greater than the neutral reference voltage, or less than or equal to the neutral reference voltage. The outputs of the comparators  424  when at a logic high (“1”) may represent that the back EMF voltage is greater than the neutral reference voltage, and when at a logic low (“0”) may represent that the back EMF voltage is less than or equal to the neutral reference voltage, or visa-versa (designer&#39;s choice). The outputs of each of the comparators  424  may thereby be used to indicate when the back EMF voltage is at its “zero” transition point or when a back EMF polarity transition occurs, and indicate same to the digital device  206 . If the digital device has analog inputs and analog-to-digital (ADC) conversion capabilities and/or voltage comparators, the external comparators may not be required. When this is the case, the outputs from the low pass filters and the neutral reference voltage from the resistors  426  and  428  may be connected directly to the analog inputs (not shown) of the digital device  206  (e.g., mixed signal device). 
         [0027]    Referring to  FIG. 5 , depicted are schematic timing and amplitude graphs of a four-pole motor showing back electromotive force (EMF) voltages at each of the three stator windings during each 60 degree commutation period. When a phase coil is not connected to the DC power source no current flows therethrough. When a phase coil is connected to the positive (DC+) power source, current flows in a positive direction for two commutation periods (120 electrical degrees), then no current flows (coil is unconnected from the DC power source) for a subsequent commutation period (60 electrical degrees), and after the unconnected commutation period the very same coil has current flow in a negative direction for two commutation periods (120 electrical degrees) when connected to the negative (DC−) power source, and then no current flows in a next commutation period (60 electrical degrees) before the aforementioned electrical cycle repeats, i.e., for another 360 degree electrical cycle. 
         [0028]    When using a sensorless BLDC motor, the back EMF voltage on the unconnected coil is transitioning from the positively driven polarity to the negatively driven polarity and does so throughout the 60 degree period when not being connected. If current is initially going into the coil when the connection is broken then the current will continue to flow thereby forward biasing a diode in parallel with the low-side drive transistor  110  presenting a voltage on the motor coil terminal equal to the negative (DC−) power source voltage plus the forward bias voltage of the diode. This negative spike persists until the energy in the coil is dissipated. 
         [0029]    A “zero crossing” is where the measured voltage at each phase coil  102  goes to substantially one-half of the DC supply voltage (in the graphs normalized to “zero”), and is illustrated by the small circles of the back EMF graphs. When the PWM duty cycle is 100% in a commutation period, the measured back EMF varies between the full positive (DC+) rail voltage and the full negative (DC−) rail voltage of the power source. When the PWM duty cycle is 50% in a commutation period, the measured back EMF varies between 50% (one-half) of the full positive (DC+) rail voltage and 50% (one-half) of the full negative (DC−) rail voltage of the power source. When the PWM duty cycle is 25% in a commutation period, the measured back EMF varies between 25% (one-half) of the full positive (DC+) rail voltage and 25% (one-half) of the full negative (DC−) rail voltage of the power source. Therefore there is a direct correlation between the PWM duty cycle applied to the two current carrying coils  102  and the measured back EMF on the unconnected coil  102 . However, the back EMF always passes through the “zero crossing” point at substantially the center (e.g., middle, half-way point) of a commutation period when the other two coils are excited (current flowing therethrough). Just at lower PWM duty cycles, there is less variation of the back EMF voltage in the commutation period. This is not problematic since the “zero crossing” point is what is of interest. 
         [0030]    It is important to remember that back EMF on the unconnected coil  102  is biased properly for detection only when the other two coils  102  are connected to the positive (DC+) and negative (DC−) power source rails and current flows through them. If there is no current flow in the two connected coils  102  at the time when a “zero crossing” should occur then the back EMF voltage at the unconnected coil  102  will not be centered relative to the reference voltage, and detection of the exact “zero crossing” will not be possible. However, missing detection of the exact “zero crossing” point in time because power drive is off (no current flow) at the instant of exact zero crossing may not be fatal so long as a change in polarity, e.g., positive to negative or visa versa, of the back EMF is determined when the power drive returns soon after zero crossing, and that this occurs close enough in time (electrical degrees) so as not to cause too great of a commutation timing error in normal operation. Instability problems do result when low duty cycle PWM signals cause significant commutation timing errors. As illustrated in the back EMF graphs shown in  FIG. 5 , “zero crossing” points occur at approximately 30 electrical degrees from a commutation period change, i.e., substantially in the center (middle) of a commutation period. Use of Hall Effect position sensors  104  ( FIG. 1 ) are preferable when low duty cycle PWM signals are used for low speed motor applications. 
         [0031]    Referring to  FIG. 6 , depicted are schematic amplitude and timing graphs of voltages at one phase of the sensorless BLDC motor during each commutation period for different PWM duty cycles, according to the teachings of this disclosure. The BLDC motor operates at rotational speeds that are dependent upon the average voltages on each stator coil  102  during appropriate 60 degree commutation periods. Direction of rotation of the motor  100  ( 200 ) is dependent upon the commutation connection order of the coils  102  to the DC power source over each (360 degree) electrical cycle. 
         [0032]    Graph  530  represents a 100 percent PWM drive duty cycle over one electrical cycle at one phase of the motor  100 . The 100 percent duty cycle will result in maximum voltages resulting in maximum rotational speed of the motor  100 . 
         [0033]    Graph  532  represents approximately a five (5) percent PWM drive duty cycle over one electrical cycle at one phase of the motor  100  or  200 . At low PWM duty cycles, less average voltages will be created and thus slower rotational speeds will result since motor speed is directly proportional to the applied voltage. The ratio of rotational speed to applied voltage is much higher in high speed motors than that of low speed motors. Therefore, relatively small applied voltages in high speed motors will still result in significantly fast speed. Reducing the voltage by PWM is limited by the drive transistors  108  and  110  and the electrical characteristics of the motor since the PWM duty cycle can only be reduced to the point where the drive pulse widths can still propagate through the low pass frequency characteristics inherent in all motor designs. PWM signals whose pulse widths are too short are either attenuated by the low-pass characteristics of the motor and/or are shorter than the switching times of the drive power transistors  108  and  110 . Reducing the PWM frequency to enable use of longer pulse widths creates audible noise disturbances from the motor. Thus, the minimum inaudible PWM frequency determines the maximum pulse widths that can be used for slow speed operation of the motor  100  or  200 . 
         [0034]    Graph  534  represents approximately a ten (10) percent PWM drive duty cycle over one electrical cycle at one phase of the motor  100  or  200 . At lower duty cycles of the PWM signal, less average voltages will be created and thus slower rotational speeds will result. However, the average drive voltage to the motor can be reduced further than is possible with the minimum inaudible PWM frequency (shown in graph  532 ) by reducing the number of PWM pulses in each commutation period. This may be accomplished by gating off some of the PWM pulses that would normally be generated, as shown in graph  532 . This allows the average drive voltage to the BLDC motor  100  or  200  to be reduced by limiting the number of PWM pulses while maintaining the PWM period and duty cycle. The use of longer PWM pulse widths (e.g., 10%) are more compatible with the motor  100  or  200  and the driver transistors  108  and  110  characteristics. Use of fewer PWM pulses in a commutation period allows lower average drive voltages (slower rotational speeds). Preferably, the PWM drive pulses may be centered on the peak back EMF in the commutation periods to keep the current-resistance (I−R) losses at a minimum and to deliver maximum torque. 
         [0035]    Note that since the PWM pulses are substantially centered within each of the commutation periods, e.g., at +/−, 30, 90, 150, 210, 270, 330 degrees (electrical timing centers). The exact electrical timing center for each of the commutation periods may be shifted slightly +/− from the +30 degree values depending upon inductive lag and motor characteristics. Commutation period timing relationships are preferably determined using the rotor position signals from the Hall Effect position sensors  104  to the digital device  106  when operating at low rotational speeds. However, since the PWM signal pulses during each commutation period are substantially centered therein, there will be back EMF excitation voltage in an unconnected coil  102  near a “zero-crossing” (e.g., near points  544 ). Therefore, even during low PWM drive duty cycles where the off times of the PWM pulses in each commutation period are significant, a “zero-crossing” (points  544 ) may be determined when the measured back EMF changes polarity (referenced to the neutral reference voltage shown in  FIG. 4 ). 
         [0036]    While embodiments of this disclosure have been depicted, described, and are defined by reference to example embodiments of the disclosure, such references do not imply a limitation on the disclosure, and no such limitation is to be inferred. The subject matter disclosed is capable of considerable modification, alteration, and equivalents in form and function, as will occur to those ordinarily skilled in the pertinent art and having the benefit of this disclosure. The depicted and described embodiments of this disclosure are examples only, and are not exhaustive of the scope of the disclosure.