Abstract:
An SRAM device of the present invention is an SRAM device, including: a plurality of bit line pairs that are arranged substantially parallel to one another and connected to different memory cells, respectively; selection means for selecting one bit line pair from among the plurality of bit line pairs; and potential holding means for holding a precharge potential of bit lines that are respectively on opposite sides of the one bit line pair with the one bit line pair being selected, wherein an interval between two adjacent bit line pairs is smaller than an interval between two bit lines of the same bit line pair.

Description:
BACKGROUND OF THE INVENTION  
         [0001]    The present invention relates to an SRAM device, and more particularly to stabilizing the operation thereof.  
           [0002]    In a conventional 6-transistor SRAM device, an interline coupling occurs between a pair of bit lines BL 1  and /BL 1 , thereby causing coupling noise. In order to suppress the coupling noise, there is a technique of shielding bit lines by, for example, providing a separate ground line Vss between the pair of bit lines BL 1  and /BL 1  in the same wiring layer. FIG. 10 illustrates a memory cell  100  of an SRAM device produced by using this technique. FIG. 11 is a cross-sectional view schematically illustrating wiring layers and connection holes in an area above three memory cells  100 . FIG. 11 is a cross-sectional view taken along line XI-XI shown in FIG. 10, schematically illustrating all the connection holes and the lines connected thereto being projected onto a plane.  
           [0003]    As illustrated in FIG. 10, a total of three lines, including two bit lines (BL 1  and /BL 1 ) and a ground line Vss, are connected to the memory cell  100 . As illustrated in FIG. 11, the lines are arranged at substantially the minimum pitch both in the bit line width direction and in the connection hole depth direction.  
           [0004]    In an SRAM device including the memory cell  100  illustrated in FIG. 10 and FIG. 11, the two bit lines BL 1  and /BL 1  are completely shielded from each other by the ground line Vss provided therebetween, thereby suppressing the coupling noise in the bit line pair. However, the distance between each of the two bit lines BL 1  and /BL 1  and the ground line Vss is short, thereby increasing the line capacitance. Particularly, the line capacitance further increases as the interval between lines decreases along with the miniaturization of memory cells. The small interval between lines increases the chance of the two bit lines BL 1  and /BLI being short-circuited with the ground line Vss due to a process dust defect. If the two bit lines BL 1  and /BL 1  are short-circuited with the ground line Vss, a short-circuit leak current flows via a precharge circuit while the two bit lines BL 1  and /BL 1  are being precharged to the power supply voltage. This leak current remains even if the two bit lines BL 1  and /BL 1  are replaced by a redundant cell.  
           [0005]    As illustrated in FIG. 11, no line is provided between the memory cell  100  and an adjacent bit line (/BL 0 , BL 2 ). Therefore, coupling noise still occurs between /BL 0  and BL 1  and between /BL 1  and BL 2 .  
           [0006]    The problem of coupling noise can be solved by providing a shielding ground line or a shielding power supply line between the two bit lines (BL 1  and /BL 1 ) of the memory cell  100  and the respective adjacent bit lines (/BL 0  and BL 2 ). Then, however, the interval between a bit line and the shielding ground line or the shielding power supply line is very small, thereby further increasing the line capacitance. This increases the charging/discharging time of the pair of bit lines (BL 1  and /BL 1 ), thereby presenting a problem that there will be an increased amount of time before a potential change of 100 mV, for example, occurs, i.e., an increased delay time until the timing at which a read sense amplifier is turned ON.  
           [0007]    In a write operation, the voltage applied to each of the two bit lines (BL 1  and /BL 1 ) dynamically changes from the power supply voltage to the ground level. Then, quite substantial coupling noise occurs between the adjacent bit lines /BL 0  and BL 1  and between the adjacent bit lines /BL 1  and BL 2 . This substantially changes the voltages being applied to the adjacent bit lines /BL 0  and BL 2 . Therefore, the information stored in a memory cell adjacent to the memory cell  100  may be destroyed.  
         SUMMARY OF THE INVENTION  
         [0008]    The present invention has been made in order to solve the problems described above, and has an object to provide an SRAM device capable of performing a stable operation.  
           [0009]    An SRAM device of the present invention is an SRAM device, including: a plurality of bit line pairs that are arranged substantially parallel to one another and connected to different memory cells, respectively; selection means for selecting one bit line pair from among the plurality of bit line pairs; and potential holding means for holding a precharge potential of bit lines that are respectively on opposite sides of the one bit line pair with the one bit line pair being selected, wherein an interval between two adjacent bit line pairs is smaller than an interval between two bit lines of the same bit line pair.  
           [0010]    By holding the precharge potential of bit line pairs that are adjacent to, and respectively on opposite sides of, a selected bit line pair, the bit lines that are adjacent to, and respectively on opposite sides of, the selected bit line pair can behave as shield lines for the selected bit line pair. Therefore, it is possible to improve the shield effect against the coupling noise between the selected bit line pair and each of the bit lines that are adjacent to, and respectively on opposite sides of, the selected bit line pair, without providing any additional elements or lines. Moreover, the precharge operation is continued for the adjacent bit line pairs, and they behave as if they were power supply lines. Therefore, it is no longer necessary to take into consideration the influence of the coupling between two adjacent bit line pairs. Thus, the interval between two adjacent bit line pairs can be reduced, whereby it is possible to increase the interval between two bit lines of the same pair. Therefore, with the SRAM device of the present invention, it is possible to reduce the capacitance occurring between two bit lines of the same pair. Thus, it is possible to reduce the coupling noise without separately providing a special-purpose shield line between the bit lines of the same pair.  
           [0011]    Since the interval between the bit lines of the same pair is large and no special-purpose shield line is provided between the two bit lines of the same pair, a short circuit will not occur between each bit line in one bit line pair and a shield line. Therefore, a short-circuit leak current is prevented from flowing via a precharge circuit while all of the bit lines are precharged to the power supply voltage.  
           [0012]    Since the interval between two adjacent bit line pairs is small, it is possible that a short-circuit occurs between two adjacent bit line pairs. However, since all the bit lines are at an equal potential when the bit lines are precharged to the power supply voltage, a short-circuit leak current does not occur due to the short-circuit.  
           [0013]    The potential holding means may hold a precharge potential of all of the plurality of bit line pairs excluding the selected bit line pair.  
           [0014]    The potential holding means may hold a precharge potential of odd-numbered bit line pairs, counting from the selected bit line pair, and may not hold a precharge potential of even-numbered bit line pairs, counting from the selected bit line pair.  
           [0015]    The number of bit line pairs whose precharge potential is held by the potential holding means may be greater than the number of bit line pairs whose precharge potential is not held by the potential holding means.  
           [0016]    The potential holding means may hold a precharge potential only in a write operation.  
           [0017]    It is preferred that the interval between two adjacent bit line pairs is smaller, and the interval between two bit lines of the same bit line pair is larger, than a thickness of each bit line of the plurality of bit line pairs.  
           [0018]    In this way, it is possible to reduce the line capacitance in each bit line pair.  
           [0019]    It is preferred that the SRAM device further includes a plurality of wiring layers, wherein one of the plurality of wiring layers in which the bit lines are provided includes no line other than the bit lines in regions above the memory cells.  
           [0020]    By providing a special-purpose wiring layer for bit lines, it is possible to ensure a large line interval between a bit line and each of two wiring layers that are respectively above and below the bit line.  
           [0021]    It is preferred that: the plurality of wiring layers include a first wiring layer, a second wiring layer, a third wiring layer and a fourth wiring layer, which are layered in this order; ground lines of the memory cells are provided in the first wiring layer and the fourth wiring layer so as to be perpendicular to the bit lines; power supply lines of the memory cells are provided in the second wiring layer and the fourth wiring layer so as to be perpendicular to the bit lines; and the bit lines are provided in the third wiring layer.  
           [0022]    In this way, the ground line and the power supply line can be used as shield lines sandwiching a bit line formed in the third wiring layer.  
           [0023]    It is preferred that in regions above the memory cells, no connection hole is provided for connecting the fourth wiring layer to other lower wiring layers including the third wiring layer.  
           [0024]    In this way, it is possible to reduce the plug and/or line in the vicinity of a bit line as compared to that in the prior art. Therefore, it is possible to reduce the capacitance of the bit line itself, the capacitance in a bit line pair, and the capacitance between a bit line pair and each of bit lines adjacent to the bit line pair.  
           [0025]    Another SRAM device of the present invention is an SRAM device, including: a plurality of bit line pairs that are arranged substantially parallel to one another and connected to different memory cells, respectively; first selection means for selecting one odd-numbered bit line pair, counting from an end bit line pair, from among the plurality of bit line pairs; first potential holding means for holding a precharge potential of even-numbered bit line pairs, counting from the end bit line pair, with the one oddnumbered bit line pair being selected; second selection means for selecting one even-numbered bit line pair, counting from the end bit line pair, from among the plurality of bit line pairs; and second potential holding means for holding a precharge potential of odd-numbered bit line pairs, counting from the end bit line pair, with the one even-numbered bit line pair being selected, wherein an interval between two adjacent bit line pairs is smaller than an interval between two bit lines of the same bit line pair.  
           [0026]    With such an SRAM device, when an odd-numbered (even-numbered) bit line pair (counting from an end bit line pair) is selected from among a plurality of bit line pairs, a precharge operation is continued for an even-numbered (odd-numbered) bit line pair. Thus, the precharge potential of bit line pairs that are adjacent to, and respectively on opposite sides of, the selected bit line pair is held. In this way, the bit lines that are adjacent to, and respectively on opposite sides of, the selected bit line pair can behave as shield lines for the selected bit line pair. Therefore, it is possible to improve the shield effect against the coupling noise between the selected bit line pair and the bit lines that are adjacent to, and respectively on opposite sides of, the selected bit line pair, without providing any additional elements or lines. Alternatively, with the SRAM device of the present invention, the bit line pair selection period may be divided in two so that data is read out from odd-numbered bit line pairs (counting from an end bit line pair) during the first half and from even-numbered bit line pairs (counting from an end bit line pair) during the second half. Thus, the bit line pair selection period may be divided into a number of sub-periods so that a plurality of bit line pairs are selected by selecting a single bit line pair in each of the sub-periods. This is suitable for a case where data that is read out and written is processed in a pipelined process, and increases the data processing speed. 
       
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS  
       [0027]    [0027]FIG. 1A and FIG. 1B are diagrams each illustrating a memory cell included in an SRAM device in one embodiment of the present invention.  
         [0028]    [0028]FIG. 2A is a diagram schematically illustrating a method for driving a 6-transistor SRAM device in one embodiment of the present invention.  
         [0029]    [0029]FIG. 2B is a diagram schematically illustrating a method for driving a conventional 6-transistor SRAM device.  
         [0030]    [0030]FIG. 3A and FIG. 3B are diagrams each illustrating a method for driving an SRAM device in one embodiment of the present invention.  
         [0031]    [0031]FIG. 4 is a diagram illustrating a method for driving an SRAM device in one embodiment of the present invention.  
         [0032]    [0032]FIG. 5A is a diagram illustrating a transistor used in a memory cell of an SRAM device in one embodiment of the present invention.  
         [0033]    [0033]FIG. 5B is a diagram illustrating the structure of a first wiring layer of a memory cell of an SRAM device in one embodiment of the present invention.  
         [0034]    [0034]FIG. 6A is a diagram illustrating the structure of a second wiring layer of a memory cell of an SRAM device in one embodiment of the present invention.  
         [0035]    [0035]FIG. 6B is a diagram illustrating the structure of a third wiring layer of a memory cell of an SRAM device in one embodiment of the present invention.  
         [0036]    [0036]FIG. 7A is a diagram illustrating a bit line arrangement in a conventional SRAM device.  
         [0037]    [0037]FIG. 7B is a diagram illustrating a bit line arrangement in an SRAM device in one embodiment of the present invention.  
         [0038]    [0038]FIG. 8A is a diagram illustrating a memory cell of an SRAM device in one embodiment of the present invention.  
         [0039]    [0039]FIG. 8B shows a diagram illustrating a matrix arrangement of memory cells illustrated in FIG. 8A, and an enlarged view of a portion of the matrix arrangement.  
         [0040]    [0040]FIG. 9 is a cross-sectional view schematically illustrating a wiring layer of an SRAM device in one embodiment of the present invention.  
         [0041]    [0041]FIG. 10 is a diagram illustrating a memory cell of a conventional SRAM device.  
         [0042]    [0042]FIG. 11 is a cross-sectional view schematically illustrating a wiring layer of a conventional SRAM device. 
     
    
     DESCRIPTION OF THE PREFERRED EMBODIMENTS  
       [0043]    An embodiment of the present invention will now be described with reference to the drawings.  
         [0044]    [0044]FIG. 1A and FIG. 1B illustrate a memory cell  10  provided in an SRAM device of the present embodiment. As illustrated in FIG. 1A and FIG. 1B, the memory cell  10  of the present embodiment includes a complementary data storage section S, a pair of bit lines (BL 1  and /BL 1 ), a word line WL, and a pair of access transistors (MN 2  and MN 3 ) connecting the pair of bit lines to the data storage section S. The complementary data storage section S includes a pair of CMOS inverters (one including MOS transistors MP 0  and MP 1 , and the other including MOS transistors MN 0  and MN 1 ) that are crosscoupled to each other.  
         [0045]    In the memory cell  10  of the present embodiment, the interval between two adjacent bit lines /BL 1  and BL 2  is small, and the interval between the pair of bit lines BL 1  and /BL 1  is larger than that between the adjacent bit lines /BL 1  and BL 2 .  
         [0046]    The SRAM device including the memory cell  10  having such a configuration is driven by a driving method to be described below. A method for driving the SRAM device of the present embodiment will now be described with reference to the drawings.  
         [0047]    [0047]FIG. 2A is a diagram schematically illustrating the method for driving the 6-transistor SRAM device of the present embodiment. FIG. 2B is a diagram schematically illustrating a method for driving a conventional 6-transistor SRAM device.  
         [0048]    As illustrated in FIG. 1B, in a memory cell of the 6-transistor SRAM device, a pair of CMOS inverter circuits are connected to each other in a flip flop configuration, and the pair of access transistors MN 2  and MN 3  are connected to the respective storage nodes, the word line WL being the gate input of each of the access transistors MN 2  and MN 3 . A data transfer operation, i.e., a read operation or a write operation, is performed between the pair of bit lines BL 1  and /BL 1  via the access transistors MN 2  and MN 3 . Only when a memory cell is selected, the word line WL is at a logical level “1”, thereby turning ON the access transistors MN 2  and MN 3 . Normally, all the bit lines provided in the SRAM device, including the pair of bit lines BL 1  and /BL 1 , are set to an equal potential before a memory cell is selected (hereinafter, this will be referred to as a “precharge” operation), so as to prevent data of the previously selected memory cell from being erroneously written to the next memory cell to be selected.  
         [0049]    In the present embodiment, data is not read out from an input/output section by all bit line pairs that are simultaneously accessed by a word line selection operation, but instead, data is read or written by those bit line pairs that are selected by a column selection operation, as illustrated in FIG. 2A. For example, the column selection operation may be an operation of selecting 1/2 (1 pair out of 2 pairs), 1/4 (1 pair out of 4 pairs), 1/8 (1 pair out of 8 pairs) or 1/16 (1 pair out of 16 pairs) of all the bit line pairs. Therefore, only the potential read out by the selected bit line pair (BL 1  and /BL 1 ) is of significance, and the potential read out by any non-selected pair of bit lines is of no significance. By utilizing this, the bit line pairs (BL 0  and /BL 0 ) and (BL 2  and /BL 2 ) adjacent to the selected bit line pair are set to an equal potential when a data read/write operation is performed from/to the input/output section. Specifically, the potential of the bit line pairs (BL 0  and /BL 0 ) and (BL 2  and /BL 2 ) is held at a precharged state until a data read/write operation is performed from/to the input/output section. In this way, it is possible to have the bit line pairs (BL 0  and /BL 0 ) and (BL 2  and /BL 2 ) behave as if they were shield lines.  
         [0050]    With the conventional driving method, the potential of the bit line pairs (BL 0  and /BL 0 ) and (BL 2  and /BL 2 ) adjacent to the selected bit line pair is not controlled in a data read/write operation from/to the input/output section. Therefore, as illustrated in FIG. 2B, when the adjacent bit lines /BL 0  and BL 2  are not at the same potential as in the precharged state, quite substantial coupling noise may occur between the bit lines /BL 0  and BL 1  and between the bit lines /BL 1  and BL 2 .  
         [0051]    With the driving method of the present embodiment, however, it is possible to improve the shield effect against the coupling noise between the selected bit line pair (BL 1  and /BL 1 ) and the adjacent bit line pairs (BL 0  and /BL 0 ) and (BL 2  and /BL 2 ), without providing any additional elements or lines.  
         [0052]    The present inventors also found the following phenomenon associated with the relationship between the number N of bit line pairs that are held at the precharged state and the number M of bit line pairs that are released from the precharged state.  
         [0053]    1) If N&gt;M, there is an increase in the DC current flowing, via a bit line, between a ground node in a memory cell accessed by a word line and a precharge power supply.  
         [0054]    2) Precharge operations are performed simultaneously during a precharge period after releasing the precharged state in a read period. Therefore, if N&lt;M, currents, such as a charge/discharge current for a bit line or a charge/discharge current for controlling a control circuit and a precharge circuit, occur within a very short period of time. Thus, an alternating current having a very short period occurs. The occurrence of the alternating current may cause substantial power supply noise.  
         [0055]    With the driving method of the present embodiment, depending on the DC current flowing along a bit line and the alternating current occurring in a period of time from the word line access period to the precharge operation, N and M can be adjusted so as to minimize the total of the DC current and the alternating current described above in 1) and 2).  
         [0056]    In order to reduce the access cycle time, it is important to complete the precharge period as soon as possible. A larger value of M requires more charge/discharge current to simultaneously bring all the bit lines to the precharged state in the precharge operation. Since the charge/discharge current occurs in a very short period of time, the current will be an alternating current with a very short period. Therefore, it takes some time to return to a stable state due to a voltage drop and voltage bouncing of a power supply line Vcc. This increases the time lag for transitioning to the next access period, thereby increasing the access cycle time.  
         [0057]    With the driving method of the present embodiment, N and M can be adjusted so that the access cycle time is reduced.  
         [0058]    Specific examples of driving methods for adjusting N and M will now be described with reference to FIG. 3A, FIG. 3B and FIG. 4.  
         [0059]    Driving Method 1  
         [0060]    [0060]FIG. 3A illustrates Driving Method 1, according to which the precharge operation is continued for all the bit line pairs other than the bit line pair (BL 1  and /BL 1 ) that is selected by a column selection operation. In other words, the selected bit line pair (BL 1  and /BL 1 ) is released from the precharged state if the bit line pairs (BL 0  and /BL 0 ) and (BL 2  and /BL 2 ) adjacent to the selected bit line pair (BL 1  and /BL 1 ) are both non-selected bit line pairs. With this method, the configuration of a precharge circuit  2  is as shown in “Case 1” in FIG. 4. With this method, all of the bit line pairs other than the bit line pairs (BL 0  and /BL 0 ) and (BL 2  and /BL 2 ) adjacent to the selected bit line pair (BL 1  and /BL 1 ) are in a non-precharged state, whereby N&lt;M (the state described above in (2)). Therefore, the method is effective in a case where the word line WL access period is long, or in a case where the bit line capacitance is small and there is little occurrence of an alternating current in a precharge operation.  
         [0061]    Driving Method 2  
         [0062]    [0062]FIG. 3B illustrates Driving Method 2, according to which the precharge operation is continued for even-numbered bit line pairs (counting from an end bit line pair) if an odd-numbered bit line pair is selected by a column selection operation, while the precharge operation is continued for odd-numbered bit line pairs (counting from an end bit line pair) if an even-numbered bit line pair is selected by a column selection operation. This method can easily be realized as shown in “Case 2” in FIG. 4 as long as one bit of the address from which a column selection signal is produced is available. In this case, N is equal to M.  
         [0063]    Driving Method 3  
         [0064]    According to Driving Method 3, only the selected bit line pair is released from the precharged state, while the precharge operation is continued for the other bit line pairs. With this method, the number of bit line pairs (of all the bit line pairs available for the column selection operation) for which the precharge operation is continued is greater than the number of bit line pairs that are released from the precharged state upon access by the word line WL, i.e., N&gt;M (the state described above in (1)). This method can easily be realized by controlling the precharge circuit  2  by using an AND circuit  3  illustrated in FIG. 4. This method provides significant effects of reducing the access cycle time, the power consumption, the power supply noise, etc., in a case where the word line WL access period is short or where the bit line capacitance is large and thus the alternating current occurring in the precharge operation is large.  
         [0065]    Driving Method 4  
         [0066]    The potential of each bit line of the selected bit line pair is rapidly changed from the power supply voltage level to the ground line level in a write operation. Therefore, there is substantial coupling noise to adjacent bit lines. According to the method shown in “Case 3” in FIG. 4, the bit line pair precharge operation is continued only during the word line WL access period in a write operation, so that N and M take different values in a read operation and in a write operation. In this way, it is possible to optimize the access cycle time, the power consumption and the power supply noise, whereby it is possible to expect greatest improvements to the problems described above.  
         [0067]    As shown in Driving Methods 1 to 4 above, the present embodiment has been described with respect to a case where a data read/write operation is performed from/to the input/output section by using bit line pairs that are selected by a column selection operation. Alternatively, the present embodiment can be applied to a special SRAM device in which the bit line pair selection period is divided in two so that data is read out from odd-numbered bit line pairs (counting from an end bit line pair) during the first half and from even-numbered bit line pairs (counting from an end bit line pair) during the second half, for example. This can be achieved only by alternately performing the control operations shown in “Case 2” in FIG. 4. Therefore, the column selection operation as used in the present embodiment may also include a column selection operation such that the bit line pair selection period is divided into a number of sub-periods so that a plurality of bit line pairs are selected by selecting a single bit line pair in each of the sub-periods. This driving method is suitable for a case where data that is read out and written is processed in a pipelined process, and increases the data processing speed.  
         [0068]    In the present embodiment, methods for driving a 6-transistor single-port SRAM device have been described. Alternatively, similar driving methods can be used for an 8-transistor 2-port SRAM device. In the case of an 8-transistor 2-port SRAM device, the bit line pairs can be grouped into two groups that do not need to be read out at the same time, wherein the precharge operation is continued for the bit line pairs of one group so that the bit line pairs behave as if they were power supply lines so as to shield the bit line pairs of the other group, thereby realizing a stable bit line access operation. The bit line pairs can be grouped into two groups so that bit line pairs associated with the same port belong to the same group. Alternatively, the bit line pair selection period can be divided in two.  
         [0069]    In the present embodiment, the precharge circuit  2  is provided for each bit line pair so that the bit lines are controlled by pairs of adjacent bit lines. Of course, a configuration such that each bit line can be controlled independently may be employed so that each single bit line on either side of the selected bit line pair may be used as a shield line. Alternatively, in a case where each precharge circuit controls a plurality of bit line pairs, a number of bit line pairs may be used as shield lines. Thus, any configuration may be employed as long as bit lines adjacent to the selected bit line pair can be used as shield lines.  
         [0070]    Next, the structure of the memory cell  10  provided in the SRAM device of the present embodiment will be described for each wiring layer.  
         [0071]    [0071]FIG. 5A is a diagram illustrating a P-type active region  12  formed in an N-well region  11  on a semiconductor substrate, an N-type active region  13 , a gate line  14 , and the word line WL. As illustrated in FIG. 5A, the load transistors MP 0 , MP 1 , MN 0  and MN 1  and the access transistors MN 2  and MN 3  are formed. Moreover, cell nodes  15  connected to the transistors, a cell node  17  connected to the power supply line Vcc, and a cell node  19  connected to the ground line Vss, are provided.  
         [0072]    [0072]FIG. 5B illustrates lines  16  for cross-coupling the cell nodes  15 , a line  18  for connecting the cell node  17  to the power supply line Vcc, and a line  20  for connecting the cell node  19  to the ground line Vss. The lines  16 ,  18  and  20  are all formed in a first wiring layer.  
         [0073]    [0073]FIG. 6A illustrates a backing line  21  for the word line WL, a line  22  for cross-coupling the cell nodes  15 , and a line  23  used for the power supply line Vcc. The backing line  21  for the word line WL, the lines  22  and  23  are all formed in a second wiring layer.  
         [0074]    [0074]FIG. 6B illustrates an arrangement of the bit lines BL 1  and /BL 1  in the SRAM device of the present embodiment. As illustrated in FIG. 6B, the bit lines BL 1  and /BL 1  are formed by using a third wiring layer, and the interval between the bit lines BL 1  and /BL 1  is larger than that in conventional SRAM devices.  
         [0075]    As can be seen from FIG. 5A, FIG. 5B, FIG. 6A and FIG. 6B, the cross-coupling connection of the cell nodes  15  is provided by the lines  16  in the first wiring layer and the lines  22  in the second wiring layer, which are perpendicular to the lines  16  in the first wiring layer. The backing line  21  for the word line perpendicular to the bit lines BL 1  and /BL 1  is provided by using the second wiring layer, and the bit lines BL 1  and /BL 1  are provided so that the bit lines BL 1  and /BL 1  are the only lines in the third wiring layer.  
         [0076]    As illustrated in FIG. 1A and FIG. 1B, the memory cell  10  of the present embodiment having such a configuration as described above includes the complementary data storage section S, the pair of bit lines (BL 1  and /BL 1 ), the word line WL, and the pair of access transistors (MN 2  and MN 3 ) connecting the pair of bit lines to the data storage section S. The complementary data storage section S includes a pair of CMOS inverters (one including the MOS transistors MP 0  and MP 1 , and the other including the MOS transistors MN 0  and MN 1 ) that are cross-coupled to each other. Particularly, as compared to a conventional SRAM device, the interval between two adjacent bit lines /BL 1  and BL 2  is small, and the interval between the pair of bit lines BL 1  and /BL 1  is larger than that between the adjacent bit lines /BL 1  and BL 2 .  
         [0077]    An SRAM device including the memory cell  10  having such a configuration is suitable for the driving methods of the present embodiment as described above, for the reasons to be described below with reference to FIG. 7A and FIG. 7B. FIG. 7A is a diagram illustrating a bit line arrangement in a conventional SRAM device, and FIG. 7B is a diagram illustrating a bit line arrangement in the SRAM device of the present embodiment.  
         [0078]    When employing the conventional driving method, in which the precharge operation is not continued for adjacent bit line pairs (see FIG. 2B), an intra-pair capacitance cintra occurring between a pair of bit lines, and an inter-pair capacitance Cinter occurring between bit line pairs, may both have a similar influence as coupling noise. Therefore, taking the worst case into consideration, it is unavoidable to have the bit lines arranged at regular intervals, as illustrated in FIG. 7A.  
         [0079]    With the driving method of the present embodiment, however, the precharge operation is continued for the adjacent bit line pairs (BL 0  and /BL 0 ) and (BL 2  and /BL 2 ) and thus the adjacent bit line pairs behave as if they were power supply lines, as illustrated in FIG. 7B. Therefore, it is no longer necessary to take into consideration the influence of the inter-line coupling between the selected bit line pair and each of the adjacent bit line pairs. Thus, the interpair capacitance Cinter does not have to be small, whereby it is possible to reduce a line interval Dinter, thus increasing the line interval Dintra between two bit lines of the same pair. Therefore, with the configuration of the memory cell  10  of the present embodiment, it is possible to reduce the intra-pair capacitance Cintra, thereby reducing coupling noise without separately providing a special-purpose shield line between the pair of bit lines (BL 1  and /BL 1 ).  
         [0080]    Since the line interval Dintra between two bit lines of the same pair is large and no special-purpose shield line is provided between the two bit lines BL 1  and /BL 1 , the two bit lines BL 1  and /BL 1  will not be short-circuited with the ground line Vss. Therefore, a short-circuit leak current is prevented from flowing via a precharge circuit while the two bit lines BL 1  and /BL 1  are precharged to the power supply voltage. Since the line interval Dinter is small, it is possible that a short-circuit occurs between adjacent bit lines of two adjacent bit line pairs (e.g., between /BL 0  and BL 1 , or between /BL 1  and BL 2 ). However, since all the bit lines are at an equal potential when the bit lines are precharged to the power supply voltage, a short-circuit leak current does not occur due to the short-circuit. Thus, a short-circuit occurring between adjacent bit lines of two adjacent bit line pairs presents no problem.  
         [0081]    In order to minimize the line capacitance in a bit line pair, it is preferred to maximize the line interval between bit lines of the same pair with respect to the bit line thickness. Specifically, in the present embodiment, the line interval in a bit line pair is larger (700 nm), and the line interval between two adjacent bit line pairs is smaller (300 nm), than the bit line thickness (540 nm where a 0.15 μm design rule is employed). Moreover, the effect of blocking electric force lines can be increased by providing a shield line in each of two wiring layers that are respectively above and below the wiring layer in which bit lines are formed. Particularly, the configuration of the memory cell  10  of the present embodiment provides significant effects when the ratio between the bit line thickness and the bit line width (aspect ratio) is greater than 2.  
         [0082]    Moreover, in the memory cell  10  of the present embodiment, an even larger line interval can be obtained between a bit line and each of two wiring layers that are respectively above and below the bit line by providing a special-purpose wiring layer for bit lines (the third wiring layer) as illustrated in FIG. 6B.  
         [0083]    [0083]FIG. 8A illustrates a fourth wiring layer used for the ground line Vss and the power supply line Vcc. FIG. 8B illustrates a substrate contact section (power supply crossing section) provided on a semiconductor substrate, with the memory cells  10  as illustrated in FIG. 8A being arranged in a matrix pattern in a region on the semiconductor substrate excluding the substrate contact section (power supply crossing section). FIG. 8B also shows an enlarged view of a portion of the structure.  
         [0084]    As illustrated in FIG. 8A and FIG. 8B, in the memory cell  10  of the present embodiment, the ground line Vss includes a line in the first wiring layer and a line in the fourth wiring layer that are perpendicular to the bit lines, and the power supply line Vcc includes a metal line in the second wiring layer and a line in the fourth wiring layer that are perpendicular to the bit lines. Therefore, the ground line Vss and the power supply line Vcc can be used as shield lines sandwiching a bit line formed in the third wiring layer.  
         [0085]    [0085]FIG. 9 is a cross-sectional view schematically illustrating wiring layers and connection holes in an area above three memory cells  10 . FIG. 9 is a cross-sectional view taken along line IX-IX shown in FIG. 8A, schematically illustrating all the connection holes and the lines connected thereto being projected onto a plane.  
         [0086]    As illustrated in FIG. 6B and FIG. 8B, lines in the first wiring layer and the fourth wiring layer are used for the ground line Vss. Moreover, lines in the fourth wiring layer used for the ground line Vss are connected, via plugs, to lines in the third wiring layer of the substrate contact section (power supply crossing section). However, as illustrated in FIG. 9, in each region above the memory cell  10 , no contact hole or via hole is provided for connecting the fourth wiring layer to the other lower wiring layers including the third wiring layer, which is used for providing bit lines. In this way, it is possible to reduce the plug and/or line in the vicinity of a bit line as compared to that in the prior art. Therefore, it is possible to reduce the capacitance of the bit line itself, the intra-pair capacitance Cintra and the inter-pair capacitance Cinter.