Abstract:
The invention relates to a driver circuit for driving a word line of a memory. The driver circuit comprises a driver unit for deactivating the word line after an access to a memory cell, a discharging means for discharging the word line, and a signal generator that generates two control signals. A first signal triggers the driver unit to deactivate the word line and triggers the discharging means to discharge the word line. A second signal triggers the discharging mean to stop discharging the word line.

Description:
CROSS-REFERENCE TO RELATED APPLICATIONS 
   This application claims foreign priority benefits under 35 U.S.C. §119 to co-pending European patent application number EP 05 000 540.4, filed Jan. 12, 2005. This related patent application is herein incorporated by reference in its entirety. 
   BACKGROUND OF THE INVENTION 
   1. Field of the Invention 
   The invention relates to driver circuits that drive word lines of memories. 
   2. Description of the Related Art 
   Until recently, a major task in the design of row decoders and their word line drivers was a fast word line activation. But new dynamic and leakage power requirements call for an optimisation of word line drivers in regard to these new constraints. In conventional row decoders, the word line deactivation occurs late compared to the ending of a read or a write operation. As a result, a lot of power is wasted because of the long time duration the memory cells are opened. 
   More recent techniques are able to minimize the word line driver gate leakage current with an automatic suppression device, but they require a local DC level controller, which increases area, adds leakage currents and is not flexible for tuning. 
   SUMMARY OF THE INVENTION 
   It is therefore an object of the present invention to provide a word line driver circuit, whose leakage power and in particular whose dynamic power is reduced compared to conventional driver circuits. A memory circuit comprising the word line driver circuit and a method for the same purpose shall be also provided. 
   The driver circuit according to the invention drives a word line of a memory. The memory can be a ROM (i.e., read only memory) or an SRAM (i.e., static random access memory). The driver circuit comprises a driver unit, a discharging means and a first signal generator. The driver unit deactivates the word line after an access to a memory cell coupled to the word line. The access to the memory cell can be a read access or a write access. The discharging means discharges the word line when the word line is deactivated. The first signal generator generates a first control signal and a second control signal. The second control signal follows the first control signal. The first control signal triggers the driver unit to deactivate the word line. Furthermore the first control signal triggers the discharging means to start discharging the word line. Once the word line is discharged, the second control signal triggers the discharging means to stop discharging the word line. Keeping the word line at a pre-determined potential is thus not the task of the discharging means, but rather a task of the driver unit. 
   In contrast to conventional driver circuits driving word lines of memories, the driver circuit according to the invention causes the discharging means to turn off as soon as the word line is discharged. This helps to reduce the overall power consumption of the driver circuit. For example, in case the discharging means is realised as a MOS transistor, the gate leakage current of this transistor is eliminated after the discharging transistor has discharged the word line. Due to the required width of the discharging transistor, the invention helps to reduce the power consumption of the driver circuit significantly. 
   Another advantage of the driver circuit according to the invention is that the word line can be deactivated and discharged as soon as the read or write operation is completed. Using a signal from an external signal generator for this purpose allows for deactivating and discharging the word line faster as it can be done by employing word line selection signals for this purpose. 
   It can be advantageously provided that the time period between the first control signal and the second control signal can be controlled. Consequently, the time period during which the discharging means is activated can be as short as necessary for discharging the word line. Thus the power consumption caused by the discharging means is reduced as much as possible. 
   Instead of generating a first and a second control signal independently, a first pulse can advantageously be utilized. The first edge of the first pulse then represents the first signal, and the second edge of the first pulse represents the second signal. 
   Apart from deactivating the word line, the driver unit also activates the word line when data shall be read from or stored into a memory cell coupled to the word line. 
   The driver unit advantageously comprises at least two driver transistors, which are coupled to the word line. The first driver transistor is turned on during an activated period of the word line and, for instance, connects the word line to a supply voltage. During a deactivated period of the word line, the first driver transistor is turned off, and a second driver transistor is turned on. During that time, the second driver transistor keeps the word line, for instance, at ground potential. 
   Advantageously, the discharging means comprises a discharging transistor coupled to the word line. 
   In accordance with one advantageous configuration of the invention, the word line can be discharged faster by the discharging means than by the driver unit. 
   This capability of the discharging means can be realised by selecting a discharging transistor with a channel width that is wide enough to conduct an appropriate current through the channel of the discharging transistor. 
   The driver transistors are advantageously controlled by the first control signal and not by the second control signal. In contrast to this, the discharging transistor is controlled by the first and the second control signals. This makes it possible to use the first control signal for deactivating the word line and for starting discharging the word line. In contrast to this, the second control signal does not reactivate the word line, but only stops discharging the word line. 
   The memory circuit according to the invention comprises a plurality a memory cells, which are organised in rows and columns. Word lines are coupled to the rows of memory cells, respectively. Moreover, a plurality of driver circuits as described above are coupled to the word lines, respectively. 
   Alternatively, it can be provided that the memory circuit comprises only one first signal generator shared by the driver circuits instead of equipping each driver circuit with its own first signal generator. 
   Furthermore, the memory circuit advantageously comprises a plurality of bit lines, a dummy bit line and a dummy word line. Each bit line is coupled to a column of memory cells. The dummy bit line and the dummy word line are coupled to dummy memory cells. The signal transmission behaviors of the dummy bit line and the dummy word line are essentially characteristic of the signal transmission behavior of the bit lines and the word lines, respectively. 
   In accordance with one advantageous configuration of the invention, the memory circuit contains a second signal generator. The second signal generator generates a third control signal that is supplied to the dummy bit line. The third control signal tracks the height of the memory. The signal outputted by the dummy bit line is used for generating the first control signal. Moreover the signal outputted by the dummy bit line is supplied to the dummy word line. This signal tracks the width of the memory and the load of the word lines. After traversing the dummy word line, this signal is used for generating the second control signal. 
   The advantage of this concept is that the signals that are responsible for resetting and discharging the word lines are generated by the memory&#39;s internal self-timing. This makes it possible to close the memory cells as soon as the read or write operation has been performed. Furthermore, tracking the width of the memory ensures that, on the one hand, the discharging means is not turned off before the word line is completely discharged, and on the other hand, the time period during that the discharging means is turned on is as short as possible. 
   In order to generate the second control signal, it can advantageously be provided that the second signal generator comprises a gate with an AND function. This gate can be implemented, for instance, as an AND or a NAND gate. The gate is fed with the output signal of the dummy bit line and the output signal of the dummy word line on its input terminals. The output terminal of the gate provides the second control signal and in particular the first control signal. 
   A memory circuit usually contains a row decoder that receives row address signals and selects one of the driver circuits according to the row address signals in order to activate the word line coupled to the selected driver circuit. According to the invention, the second signal generator generates the third control signal when the row decoder receives the row address signals. This ensures a minimal cycle time and reduces dynamic power. 
   It can be also advantageously provided that the output signal of the dummy bit line caused by the third control signal triggers the reset of a clock DFF. Since most memories are nowadays edge sensitive, a clock DFF is needed to detect the clock signal of the user. When the clock DFF is reset due to the internal self-timing of the memory, it is available for the next clock activation. The clock DFF is the central timer of the memory. It controls the pre-charging of the bit lines, the ADD, DIN and RWB latches, the row decoder and the column multiplexer that selects the word and bit lines for a read or write operation. 
   The output signal of the dummy bit line also controls a sense amplifier of the memory that is needed in case of a read access to a memory cell. In this case, the sense amplifier is coupled to the corresponding bit line. 
   In accordance with the present invention, a method of deactivating a word line of a memory is comprised of the following steps: 
   generating a first control signal that triggers the deactivation of the word line after an access to a memory cell coupled to the word line and that triggers a discharging mean to start discharging the word line; and 
   generating a second control signal that triggers the discharging mean to stop discharging the word line. 
   The method according to the invention offers the same advantages over conventional methods as the driver circuit. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
     So that the manner in which the above recited features of the present invention can be understood in detail, a more particular description of the invention, briefly summarized above, may be had by reference to embodiments, some of which are illustrated in the appended drawings. It is to be noted, however, that the appended drawings illustrate only typical embodiments of this invention and are therefore not to be considered limiting of its scope, for the invention may admit to other equally effective embodiments. 
       FIG. 1  shows a section of a conventional row decoder  1  according to prior art; 
       FIG. 2  shows diagrams illustrating the behavior of the word line WL shown in  FIG. 1  when selected and when deactivated; 
       FIG. 3  shows a section of a conventional row decoder  10  according to prior art; 
       FIG. 4  shows diagrams illustrating the behavior of the word line WL shown in  FIG. 3  when selected and when deactivated; 
       FIG. 5  shows a first exemplary embodiment of the driver circuit according to the invention; 
       FIG. 6  shows diagrams illustrating the behavior of the word line WL shown in  FIG. 5  when selected and when deactivated; 
       FIG. 7  shows a second exemplary embodiment of the driver circuit according to the invention; 
       FIG. 8  shows a memory making use of a dummy bit line according to prior art; 
       FIG. 9  shows a memory making use of a dummy bit line and a dummy word line according to prior art; 
       FIG. 10  shows a logic circuit  400  used for generating a pulse  104 ; 
       FIG. 11  shows diagrams illustrating the signals of the logic circuit  400  shown in  FIG. 10 ; and 
       FIG. 12  shows an exemplary embodiment of the memory circuit according to the invention. 
   

   DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT 
     FIG. 1  shows a section of a conventional row decoder  1  with a driver circuit according to prior art. The task of the row decoder  1  is to decode row address signals in order to select one word line WL of a ROM or an SRAM.  FIG. 1  shows, as an example, only the part of the row decoder  1  that affects a single word line WL. Thus, the entire row decoder  1  contains the components shown in  FIG. 1  for each word line WL of the memory. 
   The row decoder  1  shown in  FIG. 1  comprises a NAND gate NAND 1 , which is fed with word line selection signals WLSA, WLSB and WLSC on its input terminals. The output terminal of the NAND gate NAND 1  feeds a serial connection of two inverters INV 1  and INV 2 . The output of the inverter INV 2  controls the gate voltages of two transistors N 1  and P 1 . The transistor N 1  is a MOS transistor with an n-channel, and the transistor P 1  is a MOS transistor with a p-channel. Correspondingly, transistors having an n-channel are denoted with an N and transistors having a p-channel are denoted with a P in the following. One channel terminal of each of the transistors N 1  and P 1  is coupled to a word line WL, whereas the other connections of the transistors N 1  and P 1  are connected to ground VSS and a supply voltage VDD, respectively. 
     FIG. 2  illustrates the behavior of the word line WL in the course of a read or write access to a memory cell coupled to the word line WL. For that, the word line selection signals WLSA, WLSB, WLSC, the potential of the word line WL and an output signal DOUT of the memory are plotted against time t. A change in the output signal DOUT marks the end of a read or write access. 
   During a read or write access to a memory cell coupled to the word line WL, the word line selection signals WLSA, WLSB and WSLC are all at a logical high level. This causes the transistor N 1  to be switched off and the transistor P 1  to be on, thus applying the positive supply voltage VDD to the word line WL so that the word line WL is at a logical high level. 
   When the read or write access to the memory cell is completed, which is indicated by a transition of the output signal DOUT of the memory from a logical low level to a logical high level, the word line selection signals WLSA, WLSB, WLSC are switched back to the logical low level. Then the potential at a node A, which is the gate potential of the transistors N 1  and P 1 , returns to the logical high level and the word line WL is no longer selected, meaning that the potential of the word line WL switches back to the logical low level. 
   While the word line WL is not selected, the transistor N 1  is always switched on. This results in an increased power consumption of the row decoder  1  due to a gate leakage current of the transistor N 1  as indicated by an arrow  2  in  FIG. 1 . Since one task of the transistor N 1  is to discharge the word line WL after an access to a memory cell, the width of the transistor N 1  has to be large enough to fulfill this task. In return the large width of the transistor N 1  increases its gate leakage current. In the row decoder  1 , the width of the transistor N 1  is 10 times larger than a reference value, whereas the width of the transistor P 1  is 20 times larger than the reference value. 
   Another drawback of the row decoder  1  shown in  FIG. 1 and 2  is a long cycle time. The reason for this is that the window during that the word line WL is activated only depends on the word line selection signals WLSA, WLSB and WLSC. The word line selection signals WLSA, WLSB and WLSC come from the address predecoding stage, and they are relatively slow because they are generated from the clock DFF. This also becomes evident from  FIG. 2 . After the output signal DOUT is switched to the logical high level, a lot of time passes by and power is wasted as indicated by an arrow  3 , until the word line WL is deactivated. 
     FIG. 3  shows a section of a further conventional row decoder  10  with a driver circuit according to prior art. The row decoder  10  is very similar to the row decoder  1  shown in  FIG. 1  except for some additional transistors. The row decoder  1  comprises a NAND gate NAND 1 , inverters INV 1  and INV 2  as well as transistors N 1  and P 1  that are arranged in almost the same way as in the row decoder  1 . However, in contrast to the row decoder  1 , the task of the transistor N 1  in the row decoder  10  is only to discharge the word line WL in case the word line WL is being deactivated. For this reason, the width of the transistor N 1  is still 10 times larger than the reference value. (The width of the transistor P 1  is 20 times larger than the reference value.) But the row decoder  10  comprises a transistor N 2  in order to keep the word line WL at the ground potential VSS when the word line WL is not selected. Since a width of the transistor N 2  as large as the reference value is sufficient for keeping the word line WL at the ground potential VSS, the gate leakage current of the transistor N 2  is reduced compared to the gate leakage current of the transistor N 1  of the row decoder  1  shown in  FIG. 1 . 
     FIG. 4  illustrates the behavior of the word line WL coupled to the row decoder  10  in the course of a read or write access to a memory cell coupled to the word line WL. For that, the word line selection signals WLSA, WLSB, WLSC, the potentials at nodes A and B as well as the output signal DOUT of the memory are plotted against time t. The potential at the node A is identical to the gate potentials of the transistors P 1  and N 2 , whereas the potential at the node B gives the gate potential of the transistor N 1 . 
   Activating the word line WL for a read or write access to a memory cell is performed in the exact same manner as in the row decoder  1 . Since the transistor P 2  is on during the read or write access, the gate potentials of the transistors N 1  and N 2  are at the logical low level during that time and thus switched off. However, when the word line WL shall be deactivated, firstly the potential at the node A is switched to the logical high level as indicated in  FIG. 4  by an arrow  11 . This causes both transistors N 1  and N 2  to switch on and the transistor P 1  to switch off. Due to its large width, the transistor N 1  then discharges the word line WL and brings the word line WL to the ground potential VSS. The transistor P 2  and a serial connection INV 3  of inverters are arranged in such a way that after a certain time (determined by the serial connection INV 3  of inverters), the transistor P 2  turns off. Since the transistor N 3  is also off, the gate potential of the transistor N 1  is then floating which means that its gate is neither connected to the supply voltage VDD nor to the ground potential VSS. However, since the transistor N 3  generates a gate leakage current, the potential at the node B, which is also the gate potential of the transistor N 1 , slowly drops to the logical low level and switches the transistor N 1  off. This is indicated in  FIG. 4  by a circle  12 . During the time needed by the parasitic gate leakage current of the transistor N 3  to switch off the transistor N 1 , the transistor N 1  also produces a parasitic gate leakage current, which increases the power consumption of the row decoder  10 . 
   The disadvantages of the conventional row decoders  1  and  10  are overcome by a row decoder  100  that is partially depicted in  FIG. 5 .  FIG. 5  shows, as an example, only the part of the row decoder  100  that affects a single word line WL. The row decoder  100  comprises a driver circuit and serves as a first exemplary embodiment of the driver circuit according to the invention. 
   The row decoder  100  includes a NAND gate NAND 1 , a logic circuit  101  as well as transistors N 1 , N 2  and P 1 . Word line selection signals WLSA, WLSB and WLSC feed the input terminals of the NAND gate NAND 1 . The output terminal of the NAND gate NAND 1  and a reset terminal RSTB are connected to input terminals of the logic circuit  101 . The logic circuit  101  generates control signals for controlling the transistors N 1 , N 2  and P 1  via their gate potentials. The gate terminals of the transistors N 2  and P 1  are coupled to a node A, whereas the gate terminal of the transistor N 1  is coupled to a node B. The arrangement of the transistors N 1 , N 2  and P 2  with regard to the word line WL is identical to the arrangement in the row decoder  10  shown in  FIG. 3 . The widths of the transistors N 1  and P 1  are 10 and 20 times larger than a reference value, respectively. The width of the transistor N 2  is as large as the reference value. 
     FIG. 6  illustrates the mode of operation of the row decoder  100  in the course of a read or write access to a memory cell coupled to the word line WL. For that, the word line selection signals WLSA, WLSB, WLSC, the reset signal feeding the reset terminal RSTB, the potentials at the nodes A and B, the potential at the word line WL as well as the output signal DOUT of the memory are plotted against time t. 
   Activating the word line WL for a read or write access to a memory cell is performed in the exact same manner as in the row decoders  1  and  10  and is indicated in  FIG. 6  by arrows  102  and  103 . 
   In order to deactivate the word line WL after the end of a read or write access to a memory cell, a pulse is generated by a control unit, which is not shown in  FIG. 5 , but will be explained below in more detail. The pulse is induced in the reset terminal RSTB as indicated in  FIG. 6  by a dashed circle  104 . When not operated, the reset terminal RSTB is at a logical high level. Thus, the pulse  104  induced in the reset terminal RSTB comprises a falling edge and a subsequent rising edge. 
   The falling edge of the pulse  104  causes the node A to return to the logical high level as indicated by an arrow  105  in  FIG. 6 . Moreover, the falling edge of the pulse  104  causes the node B to leave the logical low level and go to the logical high level as indicated by an arrow  106  in  FIG. 6 . As a result, the transistors N 1  and N 2  are switched on, whereas the transistor P 1  is switched off so that the word line WL is discharged by the transistor N 1  and is kept at the ground potential VSS by the transistor N 2  as indicated by an arrow  107  in  FIG. 6 . 
   The falling edge of the pulse  104  is positioned in such a manner that the word line WL is discharged shortly after the output signal DOUT of the memory has switched from a logical low level to a logical high level. Since this transition of the output signal DOUT is a sign of the completion of the read or write access, only a very short time passes by after the completion of the read or write access until the word line WL is deactivated. Thus, the dynamic power is minimized at the end of an operating cycle by optimizing the word line window to close the memory cells as soon as the read or write operation is performed. Since the pulse  104  resetting the row decoder  100  is generated from the memory internal self-timing, the memory cells connected to the word line WL can be closed faster than using the slow word line selection signals WLSA, WLSB and WLSC. 
   Another drawback of the conventional row decoders  1  and  10  is also eliminated by the row decoder  100 , namely the gate leakage current of the transistor N 1  used for discharging the word line WL. This is realised by the rising edge of the pulse  104 . The rising edge of the pulse  104  causes the node B to return to the logical low level as soon as the word line WL has been discharged. This is marked with an arrow  108  in  FIG. 6 . As a result, the transistor N 1  is immediately turned off and cannot produce any gate leakage current any longer. 
   It is contemplated that the pulse  104  can be also inverted, meaning the rising edge of the pulse  104  is followed by the falling edge. In this case, the logic circuit  101  needs to be adapted to the inverted pulse  104 . 
   In  FIG. 7 , another row decoder  200  is shown, which serves as a second exemplary embodiment of the driver circuit according to the invention. The row decoder  200  is partially identical to the row decoder  100  shown in  FIG. 5 . The only difference between the row decoders  100  and  200  is the detailed depiction of the logic circuit  101  in  FIG. 7 . 
   In the row decoder  200 , the reset terminal RSTB is connected to the channel terminals of transistors N 4  and P 3 . The other channel terminals of the transistors N 4  and P 3  are connected to a first input terminal of a NAND gate NAND 2  and to the input terminal of an inverter INV 5 . The gate of the transistor P 3  is controlled by the output signal of the NAND gate NAND 1 , whereas the output signal of the NAND gate NAND 1  is inverted by an inverter INV 4  before it is supplied to the gate terminal of the transistor N 4 . The output signal of the inverter INV 4  also feeds the second input terminal of the NAND gate NAND 2  and controls the gate of a transistor P 5 , the channel of which is inserted between the supply voltage VDD and the first input terminal of the NAND gate NAND 2 . The output terminals of the NAND gate NAND 2  and the inverter INV 5  form the nodes A and B, respectively. 
   The circuit arrangement of the logic circuit  101  as shown in  FIG. 7  functions as illustrated in  FIG. 6 . The components of the logic circuit  101  shown in  FIG. 7  are arranged in such a way that the falling edge of the pulse  104  affects both the node A and the node B. However, the rising edge of the pulse  104  only affects the node B. 
   An additional benefit of the row decoder  200  is the ability to select the word line WL faster due to a reduced gate load on the word line activation critical path, because the gate of the transistor N 1  is no longer on this path. As the word line driver input load is reduced, it gives more flexibility to increase the length of the transistor P 1  to reduce the sub-threshold leakage current without impacting too much the access time. 
   The width of the pulse  104  is not controlled locally in the row decoder  200  meaning that no additional control logic is needed in the row decoder  200 . The pulse  104  is rather derived from the internal-self timing of the memory. One approach for generating the pulse  104  and especially for controlling its width makes use of the so-called double dummy line concept. 
   Generally, a dummy line replicates a corresponding word line or bit line. For that, the dummy line is connected to a number of dummy transistors. The number of the dummy transistors is the same as the number of transistors connected to the corresponding word line or bit line. Furthermore, the dummy line and the corresponding word line or bit line are matched to each other. Matching between these two lines means that the main characteristic structure features of both transmission lines, which impacts the line capacitance and the propagation delay of the transmission line, are identical, e.g., same length, same width, same thickness and same dielectricity of the isolation. Then the signal transmission behavior of the dummy line is essentially characteristic of the signal transmission behavior of the corresponding word line or bit line. For example, if the delay for reading the content of a memory cell via a bit line is increased, e.g., caused by semiconductor process variations, the dummy bit line reflects this delay. Then the activation of a sense amplifier can be also delayed by the same additional delay. This leads to a self-adjusting timing architecture. 
     FIGS. 8 and 9  show schematically the internal arrangement of a conventional SRAM or ROM  300  according to prior art. The memory  300  comprises an array of memory cells  301  organised in n+1 rows and n−1 to n/2 columns. Each memory cell  301  is addressed by a row address signal and a column address signal. The row address signal is decoded in a row decoder to select one of the n+1 rows. In  FIG. 8 and 9 , the row decoder is composed of several sections denoted as rowdec  0  to rowdec n. Each section rowdec  0  to rowdec n of the row decoder drives one of the word lines WL. Every section rowdec  0  to rowdec n, for example, corresponds to the section of the row decoder  10  shown in  FIG. 3 . Each row of memory cells  301  is coupled to one of the word lines. When a row is selected, the corresponding word line exhibits a logical high level. In a similar way, the column address signal is decoded in a column decoder to select one of the n−1 to n/2 columns. Each column of memory cells  301  is coupled to one of the bit lines. 
   Furthermore, the memory  300  comprises a dummy word line  302  and a dummy bit line  303 . The dummy word line  302  is connected to n+1 dummy memory cells  304 , whereas the dummy bit line  303  is connected to n−1 to n/2 dummy memory cells  304 . The dummy cells  304  are identical to the memory cells  301 . 
   In  FIG. 8 , only the dummy bit line  303  is used for tracking the height of the memory  300 . The voltage level of the dummy bit line  303  is used for resetting the clock DFF and for triggering the sense amplifier of the memory  300  in case of a read access. 
   In  FIG. 9 , both the dummy word line  302  and the dummy bit line  303  are used for tracking the width and the height of the memory  300 . 
   In  FIG. 10 , a logic circuit  400  is shown that generates the pulse  104  shown in  FIG. 6  by making use of dummy word and dummy bit lines in order to reset the word lines WL driven by the row decoders  100  and  200  shown in  FIG. 5 and 7 . The logic circuit  400  comprises inverters INV 6 , INV 7 , INV 8  and INV 9  as well as a NAND gate NAND 3 . The inverter INV 6  is fed with a signal  401  on its input terminal and produces a signal  402  on its output terminal. The output terminal of the inverter INV 6  is connected to the input terminals of the inverters INV 7 , INV 8  as well as INV 9  and is also connected to the first input terminal of the NAND gate NAND 3 . The second input terminal of the NAND gate NAND 3  is fed with a signal  404 . On the output terminals of the NAND gate NAND 3  and the inverters INV 7 , INV 8  and INV 9 , signals  405 ,  403 ,  406  and  407  are respectively generated. 
     FIG. 11  illustrates the mode of operation of the logic circuit  400 . In  FIG. 11 , the signals  401 ,  402 ,  403  and  405  are plotted against time t. 
     FIG. 12  shows the implementation of the logic circuit  400  in an SRAM or a ROM  500 . The memory  500  serves as an exemplary embodiment of the memory circuit according to the invention. Most parts of the memory  500  are identical to the memories  300  shown in  FIG. 8 and 9 . The corresponding components in  FIG. 12  are denoted with the same reference signs. The sections rowdec  0  to rowdec n of the memory  500  correspond to the circuit diagrams shown in  FIG. 5 and 7 . 
   In order to generate the pulse  104 , firstly a pulse is generated that is supplied to the dummy bit line  303 . This pulse is generated by a section rowdec dummy of the row decoder  100  or  200 , which is connected to the dummy word line  302 . The circuit diagram of the section rowdec dummy is identical to one of the circuit diagrams shown in  FIGS. 5 and 7 . In fact, the pulse feeding the dummy bit line  303  is generated when all three word line selection signals WLSA, WLSB and WLSC feeding any of the sections rowdec  0  to rowdec n become 1. At this moment, the section rowdec dummy connected to the dummy word line  302  creates a pulse. In other words, this means that every time a word line WL is selected by its word line selection signals WLSA, WLSB and WLSC, the section rowdec dummy creates a pulse that is supplied to the dummy bit line  303 . 
   After passing the dummy bit line  303 , the pulse  401  is obtained on the output terminal of the dummy bit line  303 . As shown in  FIG. 10 , the signals  406  and  407  are obtained from the pulse  401 . The signal  406  triggers the sense amplifier of the memory in case of a read access to the memory  500 , and the signal  407  resets the clock DFF. Moreover, the pulse  403  is obtained from the pulse  401 . The pulse  403  feeds the dummy word line  302  at its input terminal. After passing the dummy word line  302 , the pulse  404  is obtained at the output terminal of the dummy word line  302 . 
   The pulse  402  obtained after traversing only through the dummy bit line  303  and the pulse  404  obtained after additionally traversing through the dummy word line  302  feed the input terminals of the NAND gate NAND 3 . As a result, the NAND gate NAND 3  outputs a pulse  405  as shown in  FIG. 11 . In  FIG. 11 , arrows  408  and  409  also indicate how the pulse  402  forms the falling edge of the pulse  405  and how the pulse  404  forms the rising edge of the pulse  405 . Finally, the pulse  405  is used to feed the reset terminals RSTB of the row decoders  100  and  200  shown in  FIGS. 5 and 7 . Consequently, the pulses  405  and  104  are identical. 
   It can be provided that the pulse  405  is not only supplied to the section of the row decoder  100  or  200  with the activated word line WL, but that the pulse  405  is supplied to all sections rowdec  0  to rowdec n. 
   The memory  500  is advantageous over the conventional memory  300  because the pulse  104 , which resets and discharges the word lines WL, is generated by the memory&#39;s internal self-timing. Tracking the height of the memory  500  by employing the dummy bit line  303  makes it possible to close the memory cells  301  as soon as the read or write operation has been performed. Furthermore, tracking the width of the memory  500  by using the dummy word line  302  ensures that, on the one hand, the discharging transistor N 1  is not turned off before the word line WL is completely discharged, and on the other hand, the time period during which the discharging transistor N 1  is turned on is as short as possible. 
   While the foregoing is directed to embodiments of the present invention, other and further embodiments of the invention may be devised without departing from the basic scope thereof, and the scope thereof is determined by the claims that follow.