Abstract:
The present invention is a dual mode LNA that can operate in either normal mode or low-gain mode, which has been designed to maintain a constant input impedance when switching between the two modes of operation. Maintaining constant input impedance is called a dynamic match. The LNA has been designed to maintain a constant bandwidth when switching between normal and low-gain modes of operation. Also, the LNA has been designed to consume much less average current when operating in the low-gain mode.

Description:
This application claims the benefit of U.S. provisional patent application Ser. No. 60/790,720, filed Apr. 10, 2006, which is incorporated herein by reference in its entirety. 

   FIELD OF THE INVENTION 
   The present invention relates to Low Noise Amplifiers (LNAs) and mixers used in Radio Frequency (RF) communications circuitry, which is used in communications systems. 
   BACKGROUND OF THE INVENTION 
   LNAs are commonly used in RF circuits when small RF signals need to be amplified for further processing. A typical application is in the front end of an RF receiver. An LNA may be the first active component in the receiver&#39;s signal path. In many applications, RF receivers must be able to function over a wide dynamic range of received signals; therefore, an LNA in the front end of such an RF receiver must be able to function over a wide dynamic range. An operating range between −100 dbm to −25 dbm is not unusual. 
   One design challenge occurs when an LNA is designed with sufficient RF gain to amplify the smallest signals, such as signals at −100 dbm. When the LNA then receives a large signal, such as signals at −25 dbm, the LNA or some of the downstream circuitry can become overloaded, driven into compression or saturation. One way to resolve this issue is to design an LNA with two modes of operation: a normal mode and a low-gain mode. In normal mode, the LNA operates with its maximum RF gain, which is sufficient to amplify the smallest signals. In low-gain mode, the LNA operates with reduced RF gain such that the circuitry is not overloaded. The low-gain mode is automatically selected when the LNA is receiving relatively large RF signals, such as those greater than −60 dbm. 
   A conventional single-ended cascode LNA  10  is shown in  FIG. 1 . In this example, N-Channel Metal Oxide Semiconductor Field Effect Transistors (N-MOSFETs) are used; however, other technologies, such as Junction Field Effect Transistors (JFETs) or bi-polar transistors, have also been used in LNA designs. The LNA  10  is constructed of a cascode transistor  12 , which is used to increase both the output-to-input isolation and the output impedance; a gain transistor  14 , which amplifies the RF input signal and sets the DC current level of the LNA  10 ; a load inductor  16 ; and a source inductor  18 , which helps determine the input impedance of the LNA  10 . The input impedance of the LNA  10  is determined by a combination of the gate-to-source capacitance  20  of the gain transistor  14 , the source inductor  18 , and the gain characteristics of the gain transistor  14 . During normal operation, the DC current level of the LNA  10  is set by applying a DC voltage, called Vbias 1 , to the gate of the gain transistor  14  through a first bias resistor R 1 , and a DC voltage, called Vbias 2 , to the gate of the cascode transistor  12 . The RF input signal to the LNA  10  is applied to the gate of the gain transistor  14 . The RF output from the LNA  10  is taken from the drain of the cascode transistor  12 . Normally, the gain transistor  14  functions in its saturated operating region. 
   A conventional differential cascode LNA  22  is shown in  FIG. 2 . A differential LNA  22  amplifies the difference between two input signals to create two amplified differential output signals. This LNA design essentially functions as two symmetrical, single-ended designs combined to form one differential design. One of the single-ended designs is arbitrarily designated as the positive side of the LNA  22 , and the other single-ended design is arbitrarily designated as the negative side of the LNA  22 . In this example, N-MOSFETs are used. The LNA  22  is constructed of a positive side cascode transistor  24  and a negative side cascode transistor  26 , both of which are used to increase the isolation of their respective sides of the LNA  22 ; a positive side gain transistor  28  and a negative side gain transistor  30 , both of which amplify the RF input signal of their respective sides; a center-tapped load inductor  32 ; and a center-tapped source inductor  34 , which helps determine the input impedance of the LNA  22 . During normal operation, the DC current level of the LNA  22  is set by applying a DC voltage, called Vbias 2 , to the gates of the cascode transistors  24 ,  26 , and a DC voltage, called Vbias 1 , to the gates of the gain transistors  28 ,  30  through a second bias resistor R 2  and a third bias resistor R 3 . The differential RF input signal to the LNA  22  is applied between the gates of the positive side gain transistor  28 , and the negative side gain transistor  30 . The RF output from the LNA  22  is taken from the drains of the positive side cascode transistor  24  and the negative side cascode transistor  26 . Normally, the positive side gain transistor  28 , and the negative side gain transistor  30  function in their saturated operating regions. 
   Several characteristics are desirable in a dual mode LNA. Since the matching circuitry connected to the input of an LNA is often a fixed impedance, it is desirable for the input impedance of the dual mode LNA to remain constant when switching between the two modes of operation. It is desirable for both modes of an LNA to function over the same operating frequency, which is a function of the LNA&#39;s bandwidth. Also, it is desirable for the average current consumption of an LNA to be as small as possible. 
   There are several conventional methods for implementing a low-gain mode; however, each of them has shortcomings. One method is to reduce the DC operating current level of the LNA by reducing Vbias 1 . This method has the benefit of reducing LNA gain and current consumption in low-gain mode; however, the LNA&#39;s cut-off frequency and the real part of the LNA&#39;s input impedance are also reduced, therefore, the input impedance is different for each mode of operation. A second method is to use some type of low-gain circuit such as a MOS bypass switch between input and output. This method does have the advantage of reduced average current consumption in bypass mode; however, such circuits have gain loss through the switch when they are in bypass mode, and when the mode is switched, the input impedance is changed and the phase of the RF signal is changed abruptly. A third method is to use a steering current circuit to divert current from the gain transistor(s). This method does allow for precise control of LNA gain in low-gain mode and has constant input impedance at normal and low-gain modes; however, average current consumption remains unchanged in low-gain mode. 
   SUMMARY OF THE INVENTION 
   The present invention is a dual mode LNA that can operate in either normal mode or low-gain mode, which has been designed to maintain the input impedance close to a matching point when switching between the two modes of operation. Maintaining input impedance close to a matching point is called a dynamic match. Also, the LNA has been designed to consume less average current and lower gain when operating in the low-gain mode. 
   In one embodiment, the present invention is implemented using two parallel cascode transistor circuits and one center-tapped source inductor to create a single-ended LNA. During the normal mode of operation, both cascode circuits are active to provide sufficient gain to amplify small RF signals. During the low-gain mode of operation, one of the cascode circuits is powered down. This reduces the gain of the LNA, and reduces the average current consumption of the LNA. The LNA input impedance remains close to the matching point between normal mode and low-gain mode by the addition of an inductor between the common source or emitter elements of the two cascode circuits. The addition of the inductor compensates for the impedance change by the gate capacitance of the off-transistor at the input node. The phase of the RF output signal changes little by switching between normal and low-gain modes. 
   In another embodiment, the present invention is implemented using a positive side of two parallel cascode circuits and a negative side of two parallel cascode circuits to create a differential LNA. 
   The present invention can be implemented using any transistor technology such MOSFET technology, JFET technology, or bipolar technology. The matching point may be substantially 50 ohms. 
   Those skilled in the art will appreciate the scope of the present invention and realize additional aspects thereof after reading the following detailed description of the preferred embodiments in association with the accompanying drawing figures. 

   
     BRIEF DESCRIPTION OF THE DRAWING FIGURES 
     The accompanying drawing figures incorporated in and forming a part of this specification illustrate several aspects of the invention, and together with the description serve to explain the principles of the invention. 
       FIG. 1  shows a conventional single-ended cascode LNA, which is one example of prior art. 
       FIG. 2  shows a conventional differential cascode LNA, which is another example of prior art. 
       FIG. 3  shows one embodiment of the present invention implemented in a dual mode single-ended cascode LNA using N-MOSFETs as the active elements. 
       FIG. 4  shows another embodiment of the present invention implemented in a dual mode differential cascode LNA using N-MOSFETs as the active elements. 
       FIG. 5  shows one application of the present invention used in the front-end of an RF receiver. 
       FIG. 6  shows another application of the present invention used as part of a mobile terminal. 
   

   DETAILED DESCRIPTION OF THE INVENTION 
   The embodiments set forth below represent the necessary information to enable those skilled in the art to practice the invention and illustrate the best mode of practicing the invention. Upon reading the following description in light of the accompanying drawing figures, those skilled in the art will understand the concepts of the invention and will recognize applications of these concepts not particularly addressed herein. It should be understood that these concepts and applications fall within the scope of the disclosure and the accompanying claims. 
   One embodiment of the present invention is a dual mode single-ended cascode LNA  36  using N-MOSFETs as the active elements as shown in  FIG. 3 . A main cascode transistor  38  and main gain transistor  40  form the main cascode circuit, while a normal mode cascode transistor  42  and normal mode gain transistor  44  form the normal mode cascode circuit with high gain. A common load inductor  46  is connected to both cascode circuits. 
   The DC current levels of the main cascode and normal mode circuits are set by applying a DC voltage, called Vbias 1 , to the main gain transistor  38  and the normal mode gain transistor  44  through a fourth bias resistor R 4 . The main cascode circuit is functional in both normal and low-gain modes of operation. The normal mode cascode circuit is functional only during the normal mode of operation and not during low-gain mode. The DC current level of the normal mode cascode circuit is set by applying a DC voltage to the normal mode gain transistor  44 . The DC voltage applied to the gate of the normal mode cascode transistor  42  is called mode select. During low-gain mode of operation, mode select is zero volts, which turns off the normal mode cascode transistor  42  and the normal mode gain transistor  44 . This effectively powers down the normal mode cascode circuit. During normal mode of operation, mode select is similar in value to Vbias 2 . 
   During normal mode of operation, both the main gain transistor  40  and the normal mode gain transistor  44  work together to form an amplifying element to amplify the RF input signal. During low-gain mode of operation, only the main gain transistor  40  works as the amplifying element to amplify the RF input signal. The gain of an N-MOSFET decreases as the width of the N-MOSFET decreases. This causes a gain reduction during low-gain mode due to the reduction of the effective width of the amplifying element since only one gain transistor is operational. 
   During normal mode of operation, the input impedance of the LNA  36  is determined by a combination of a gate to source capacitance  48  of the main gain transistor  40 , a gate to source capacitance  50  of the normal mode gain transistor  44 , a low-gain mode compensation inductor  52 , a source inductor  54 , gain characteristics of the main gain transistor  40 , and gain characteristics of the normal mode gain transistor  44 . During low-gain mode of operation, the input impedance of the LNA  36  is determined by the above factors minus the gain characteristics of the normal mode gain transistor  44 . The values of the low-gain mode compensation inductor  52  and the source inductor  54  are chosen to yield the desired LNA input impedance during normal mode of operation. The ratio of the value of the low-gain mode compensation inductor  52  to the value of the source inductor  54  are chosen such that the LNA input impedance during normal mode of operation is identical to the LNA input impedance during low-gain mode of operation, which provides the dynamic match aspect of the present invention. The low-gain mode compensation inductor  52  is compensating for the gate to source capacitance  50  of the normal mode gain transistor  44  during low-gain mode. 
   Both cascode circuits are designed with the same cut-off frequency; therefore, the transistor current gain will be identical for either mode of operation. Since the normal mode cascode circuit is effectively powered down during low-gain mode of operation, the average current consumption of the LNA can be significantly reduced. A reduction of up to 80% is possible. 
   Another embodiment of the present invention is a dual mode differential cascode LNA  56  employing N-MOSFETs as the active elements as shown in  FIG. 4 . The dual mode differential LNA  56  amplifies the difference between two input signals to create two amplified differential output signals. This LNA  56  design essentially functions as two symmetrical dual mode single-ended designs combined to form one differential design. One of the single-ended designs is arbitrarily designated as the positive side of the LNA  56 , and the other single-ended design is arbitrarily designated as the negative side of the LNA  56 . Each side of the LNA  56  is comprised of a main cascode circuit and a normal mode cascode circuit, similar to the cascode circuits in the previous embodiment. The LNA  56  is constructed of a positive side main cascode transistor  58  and a negative side main cascode transistor  60 , both of which are used to set the DC current level in the main cascode circuits on their respective sides of the LNA  56 . The LNA  56  also employs a positive side main gain transistor  62 , a positive side normal mode gain transistor  64 , a negative side main gain transistor  66 , and a negative side normal mode gain transistor  68 , all four of which amplify the RF input signal on their respective sides during normal mode operation. The LNA  56  also employs a positive side normal mode cascode transistor  70  and a negative side normal mode cascode transistor  72 , both of which are used to set the DC current level in the normal mode cascode circuits on their respective sides of the LNA  56 . The LNA  56  employs a center-tapped load inductor  74 , a center-tapped source inductor  76 , a positive side low-gain mode compensation inductor  78 , and a negative side low-gain mode compensation inductor  80 , all four of which are used to help determine the input impedance of the LNA  56 . 
   During normal mode of operation, the DC current level of the cascode circuits in the LNA  56  are set by applying a DC voltage, called Vbias 1 , to the gates of the gain transistors  62 ,  64 ,  66 ,  68  through a fifth bias resistor R 5  and a sixth bias resistor R 6 . The DC current level of the normal mode cascode circuits in the LNA  56  are set by applying a DC voltage, called mode select, which is similar in value to Vbias 2  to the gates of the normal mode cascode transistors  70 ,  72 . During low-gain mode of operation, mode select is zero volts, which turns off both normal mode cascode transistors  70 ,  72 . This effectively powers down the normal mode cascode circuits. 
   The differential RF input signal to the LNA  56  is applied between the gates of the positive side gain transistors  62 ,  64 , and the gates of the negative side gain transistors  66 ,  68 . The RF output from the LNA  56  is taken from the drains of the positive side cascode transistors  58 ,  70  and the negative side cascode transistors  60 ,  72 . Normally, the gain transistors  62 ,  64 ,  66 ,  68  function in their saturated operating regions. 
   The center-tapped load inductor  74  could be replaced in the design with two separate inductors. The center-tapped source inductor  76  could also be replaced in the design with two separate inductors. The center-tapped source inductor  76 , the positive side low-gain mode compensation inductor  78 , and the negative side low-gain mode compensation inductor  80  could be replaced in the design with a single 5-lead inductor with the appropriate taps. 
   LNAs are commonly used in the front ends of RF receivers. One example of such an application is shown in  FIG. 5 . An RF receiver  82  utilizes a dual mode single-ended cascode LNA  84  in its front end. A receiving antenna  86  is connected to a receive/transmit RF switch  88 . The receive side of the receive/transmit RF switch  88  feeds a matching network  90 , which then feeds the RX input to the dual mode single-ended cascode LNA  84 . The output of the dual mode single-ended cascode LNA  84  is connected to a bandpass filter (BPF)  92 , which then feeds a quadrature RF mixer (MIX)  94 . The quadrature RF mixer  94  and subsequent downstream receiver circuitry is comprised of a Q side and an I side. 
   The frequency reference inputs to the quadrature RF mixer  94  are fed from a frequency synthesizer, which is comprised of a phase locked loop (PLL)  96 , feeding a voltage controlled oscillator (VCO)  98 , feeding a frequency divider (% 2)  100 . The quadrature RF mixer  94  down converts the received RF signal into an intermediate frequency, or into a baseband frequency, depending on the application. The outputs of the quadrature RF mixer  94  feed low pass filters (LPF)  102 , which then feed the inputs of a quadrature automatic gain control amplifier (AGC)  104 . The output signals from the AGC  104  feed other downstream receiver circuitry. 
   One function of the AGC  104  is to adjust its gain such that a constant output signal level is maintained. By measuring the amount of gain needed, the magnitude of the input signal level can be inferred. The AGC  104  feeds gain information to receive signal strength circuitry (RSS)  106 , which generates receive signal strength information using the gain information and the mode status of the dual mode single-ended cascode LNA  84 . 
   Receive signal strength information is then fed into mode select circuitry  108 , which uses the information to control whether the dual mode single-ended cascode LNA  84  is operating in normal mode or low-gain mode. The mode select circuitry  108  drives the mode select input to the dual mode single-ended cascode LNA  84 . When the mode select input is driven to zero volts, low-gain mode is selected. When the mode select input is driven to the appropriate bias voltage, normal mode is selected. The receive signal strength circuitry  106 , the mode select circuitry  108 , or both, may utilize micro-processors in their functions. 
   Another application example of an LNA is its use in a mobile terminal  110 . The basic architecture of the mobile terminal  110  is represented in  FIG. 6  and may include a receiver front end  112 , a radio frequency transmitter section  114 , an antenna  116 , a duplexer or switch  118 , a baseband processor  120 , a control system  122 , a frequency synthesizer  124 , and an interface  126 . The receiver front end  112  receives information bearing radio frequency signals from one or more remote transmitters provided by a base station. A dual mode LNA  128  amplifies the signal. A filter circuit  130  minimizes broadband interference in the received signal, while downconversion and digitization circuitry  132  downconverts the filtered, received signal to an intermediate or baseband frequency signal, which is then digitized into one or more digital streams. The receiver front end  112  typically uses one or more mixing frequencies generated by the frequency synthesizer  124 . The baseband processor  120  processes the digitized received signal to extract the information or data bits conveyed in the received signal. This processing typically comprises demodulation, decoding, and error correction operations. As such, the baseband processor  120  is generally implemented in one or more digital signal processors (DSPs). The downconversion and digitization circuitry  132  measures the strength of the received signal and selects the appropriate mode of operation for the dual mode LNA  128 . 
   On the transmit side, the baseband processor  120  receives digitized data, which may represent voice, data, or control information, from the control system  122 , which it encodes for transmission. The encoded data is output to the transmitter  114 , where it is used by a modulator  134  to modulate a carrier signal that is at a desired transmit frequency. Power amplifier circuitry  136  amplifies the modulated carrier signal to a level appropriate for transmission, and delivers the amplified and modulated carrier signal to the antenna  116  through the duplexer or switch  118 . 
   A user may interact with the mobile terminal  110  via the interface  126 , which may include interface circuitry  138  associated with a microphone  140 , a speaker  142 , a keypad  144 , and a display  146 . The interface circuitry  138  typically includes analog-to-digital converters, digital-to-analog converters, amplifiers, and the like. Additionally, it may include a voice encoder/decoder, in which case it may communicate directly with the baseband processor  120 . The microphone  140  will typically convert audio input, such as the user&#39;s voice, into an electrical signal, which is then digitized and passed directly or indirectly to the baseband processor  120 . Audio information encoded in the received signal is recovered by the baseband processor  120 , and converted by the interface circuitry  138  into an analog signal suitable for driving the speaker  142 . The keypad  144  and display  146  enable the user to interact with the mobile terminal  110 , input numbers to be dialed, address book information, or the like, as well as monitor call progress information. 
   Those skilled in the art will recognize improvements and modifications to the embodiments of the present invention. All such improvements and modifications are considered within the scope of the concepts disclosed herein and the claims that follow.