Abstract:
A method for setting opto-sensor detection sensitivity in a projection video display comprising the steps of sequentially generating video signals of different colors for illuminating a sensor with video images of the video signals. In responsive to the video signals automatically selecting respective detection thresholds. Sequentially detecting sensor signals in excess of the respective detection thresholds. Coupling the detected sensor signals for automated adjustment of the projection video display.

Description:
FIELD OF THE INVENTION 
   This invention relates to the field of video projection display and in particular to processing raster sensing signals. 
   BACKGROUND OF THE INVENTION 
   In a projection video display, geometric raster distortions result from the physical placement of the cathode ray display tubes. Such raster distortions are exacerbated by the use of cathode ray tubes with curved, concave phosphor surfaces and the inherent magnification in the optical projection path. The projected image is composed of three scanning rasters which are required to be in register one with the other on a viewing screen. The precise overlay of the three projected images requires the adjustment of multiple waveforms to compensate for geometrical distortion and facilitate the superimposition of the three projected images. However, manual alignment of multiple waveforms is labor intensive during manufacturing, and without the use of sophisticated test equipment may preclude setup at a user location. An automated convergence system simplifies manufacturing alignment and facilitates user location adjustment by using raster edge measurement at peripheral display screen locations to determine raster size and convergence. Such an automated convergence system relies on sensors, located at screen edge locations, being illuminated by a projected setup marker M. The intensity of illumination at each sensor may vary greatly for a number of reasons as discussed in U.S. Pat. No. 6,392,612 titled Opto Sensor Signal Current Detector which is hereby incorporated by reference. Thus to avoid generating erratic signals from weak or poorly illuminated sensors it is advantageous to apply differing amounts of detection sensitivity in the form of a sensor signal detection threshold. To reduce alignment time an accelerated sequence is required where detection sensitivity differences are controllably selected in accordance with the color of the projected setup marker image 
   SUMMARY OF THE INVENTION 
   A method for setting opto-sensor detection sensitivity in a projection video display comprises the steps of sequentially generating video signals of different colors for illuminating a sensor with images of the video signals. Responsive to the video signals respective detection thresholds are automatically selected. Sensor signals in excess of the respective detection thresholds are sequentially detected. The detected sensor signals are coupled for automated adjustment of the projection video display. In a corresponding inventive circuit arrangement, a video signal generated for automated alignment, is coupled to a video amplifier comprising first and second transistors configured as a cascode amplifier and coupled to a display device. A time constant network is coupled to the first and second transistors for developing a control voltage responsive to the video signal. A third transistor is responsive to the control voltage and is switched between conduction and non-conduction responsive to a presence and absence of the video signal. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
       FIG. 1  is a simplified front view of a projection video display. 
       FIG. 2  is a schematic diagram of inventive arrangements for controlling a sensor signal detection threshold in accordance with a projected video image color. 
       FIGS. 3A-G  show waveform signals at various locations within the inventive arrangement shown in  FIG. 2 . 
   

   DETAILED DESCRIPTION 
     FIG. 1  illustrates a front view of a video projection display apparatus. The projection display comprises a plurality of cathode ray tubes with raster scanned images which are projected on to screen  700 . A cabinet C supports and surrounds screen  700  and provides a picture display area  800  which is slightly smaller than the screen. Screen  700  is depicted with a broken line to indicate an edge area which is concealed within cabinet C and which may be illuminated with raster scanned images when operated in an overscan mode as indicated by area OS. Photo sensors S are located adjacent to the periphery of screen  700  within the concealed edge area and outside viewed area  800 . However, raster scanned images can also be projected to produce a picture display on a screen or surface which is not suspended within or partially concealed by a cabinet. This method of picture display is known as a front projection display. In a front projection arrangement photo sensors are located as described previously, but in an unconcealed position adjacent to the periphery of screen. Operation of an automatic convergence correction system which will be described is equally applicable to front or back display projection. 
   Eight sensors are shown in  FIG. 1 , positioned at the corners and at the centers of the screen edges. With these sensor positions it is possible to measure an electronically generated test pattern, for example video block M, to determine picture width and height and certain geometric errors, for example, rotation, bow, trapezium, pincushion etc., and thereby align the displayed images to be superimposed one with the other over the whole of the screen area. Measurements are performed in both horizontal and vertical directions in each of the three projected color images thus yielding at least forty eight measured values. 
   Operation of the measurement and alignment system is explained in U.S. Pat. No. 6,392,612 titled Opto Sensor Signal Current Detector which is hereby incorporated by reference. However, in simple terms, three cathode ray tubes, R, G and B form raster scanned monochromatic color images which are directed through individual lens systems to converge and form a single display image  800  on screen  700 . Each cathode ray tube is equipped with four coil sets which provide horizontal and vertical deflection and horizontal and vertical convergence. The deflection coil sets are driven with deflection waveform signals that are controlled in amplitude and waveshape and synchronized with the signal source selected for display. Exemplary green channel horizontal and vertical convergence coils are driven with convergence correction waveform signals which may be considered representative of DC and AC convergence signals, for example static and dynamic convergence. However, these functional attributes may be facilitated, for example by modifying all measurement location addresses by the same value or offset to move the complete raster and achieve an apparent static convergence or centering effect. Similarly, a dynamic convergence effect may be produced by modification of the location address of a specific measurement location. Correction waveform signals for the green channel are generated by exemplary digital to analog converters which convert digital values read from memory. 
   Video display signals RGB, are derived from either a user selected input video selector or from electronically generated video information, for example, menu, or setup signals which may be combined for display by an on screen display generator. During automated sensitivity calibration or convergence alignment, a video generator forms an exemplary calibration video test signal comprising an exemplary black level signal with a monochrome rectangular block M having a predetermined video amplitude value. The video test signal including block M is coupled, for example to a cathode of a specific cathode ray tube and is automatically positioned by determining horizontal and vertical timing within the raster such that when projected, block M illuminates an exemplary sensor S 1 , as depicted in  FIG. 1 . 
   To facilitate adjustment and alignment of the three color images, setup block M is generated as described and coupled in turn to each CRT. In  FIG. 1  test pattern block M is shown approaching sensor S 1 , and as previously mentioned each sensor may be illuminated by the timed generation of the marker block within a video signal projected with an overscanned raster, or by positioning the scanned raster such that marker block M lights sensor S 1 . Each sensor generates a substantially linear photo generated signal in proportion to the intensity of the incident illumination. However, the intensity of illumination at each individual sensor may vary greatly and in prior automatic set up arrangements each sensor was evaluated for sensitivity in terms of signal output level for each color illumination to ensure that the detected edge of block M is similar for each color. In a prior arrangement alignment of detector sensitivity required about 5 seconds. Furthermore, in addition to detector sensitivity the video level of display marker block M was also capable of setting to a specific value setting for each color to ensure that all sensors could be lit or illuminated. 
   Subsequent system refinement has shown that detector sensitivity can be set to a fixed, color specific, constant value derived in accordance with the relative phosphor persistence. For example, because the blue phosphor has least persistence and consequently generates the brightest image flashes it thus requires the greatest reduction in detector sensitivity. Conversely, the green phosphor has the longest persistence and flashes dimly and hence requires the greatest detector sensitivity. The red phosphor has a persistence which is between that of the blue and green phosphors and requires a corresponding intermediate detector sensitivity. In addition it has been discovered that marker brightness or marker video level adjustment can provide sufficient compensation range to correct for component aging. This simplification is possible because the alignment system is differential and insensitive to edge detection matching between colors. It is sufficient that the edge detection for each color can be repeated with subsequent measurements. 
   The circuit arrangement of  FIG. 2  shows the advantageous sensor signal detector described previously where a predetermined threshold for sensor signal detection is set for each color. In addition the color specific thresholds are automatically selected by the video alignment marker block signal M which is coupled in turn to each cathode ray tube. In  FIG. 2  screen periphery sensors S 1 -S 8  are depicted with a parallel connection in dashed block  100 . A projected image of video marker block M is illustrated to be incident on sensor S 1  which causes a sensor signal Iill to be generated. Sensor signal Iill is coupled to sensor amplifier U 1 , depicted in block  200 , via a low pass fitter formed by series connected resistor R 1  and capacitor C 1  coupled to signal ground. 
   A detailed description of sensor amplifier U 1  is provided in U.S. patent application Ser. No. 09/657,647. However, in simple terms the use of differential amplifier U 1  provides both amplification of the wanted sensor signal Iill with rejection of unwanted crosstalk signal components. Sensor signal Iill is coupled to the inverting input amplifier U 1 , and also to the non-inverting input via resistor R 2 . Resistors R 3  and R 4  form a potential divider from the negative power supply to ground to provide a bias potential to the non-inverting input. A parallel connected arrangement of capacitor C 2  and resistor R 5  provide feedback from the output of amplifier U 1  to the inverting input. The filtered and amplified sensor signal Isen is output from amplifier U 1  via capacitor C 3  and resistor R 6  connected in series. 
   Detection of the filtered and amplified sensor signal Isen is performed in block  300  which is described in detail in U.S. Pat. No. 6,392,612 which is hereby incorporated by reference. However, in simple terms transistors Q 1  and Q 2  form a cascode amplifier which is switched between conduction and non-conduction in accordance with the amplitude of the sensor signal Isen from amplifier U 1 . A signal Iref is generated by transistor Q 3  and coupled to the junction of resistor R 6  and resistor R 7  at the base of transistor Q 1 . Signal Iref is selected to have a value such as to cause transistor Q 1  to be in saturated conduction by signal Isw until sensor signal Isen, from amplifier U 1 , is of sufficient amplitude to reduce the amplitude of signal Isw and cause transistor Q 1  to be non-conductive. Thus, transistor Q 1  forms a sensor signal detector with conduction/non-conduction, or sensor signal detection threshold determined by signal Iref from transistor Q 3  collector. Furthermore, signal Iref is selectably determined in accordance with video derived control signals formed in block  400  and coupled to transistor Q 3  emitter, as will be described. 
   When no sensors are illuminated by marker M, signal Isw turns on transistor Q 1  which in turn causes transistor Q 2  to turn on with the collector assuming a nominally ground potential. A detected sensor signal is formed at the collector of transistor Q 2  where nominally zero volts indicates an unlit sensor condition and positive voltage equal to the base emitter voltage of transistor Q 4  represents a lit sensor. Transistors Q 4  and Q 5  form a pulse stretching filter which ensures a minimum detected sensor pulse duration of a few microseconds. The detected and stretched sensor signal is output from transistor Q 5  collector as signal  202  for coupling to an automation system controller which is not illustrated. 
   Operation of the circuit arrangement of  FIG. 2 , block  300  is described in detail in U.S. Pat. No. 6,392,612. However, in simple terms transistors Q 1 , Q 2  and Q 3  provide a sensor signal detector with a plurality of selectable detection thresholds which in addition include a predetermined detection turnoff threshold hysteresis. The magnitude of threshold signal Iref is determined by the base to emitter voltage of current source transistor Q 3 . This in turn is related the value of emitter resistor R 11  which couples the emitter of transistor Q 3  to a positive supply voltage. In a prior arrangement, control of threshold signal Iref was provided by a digital to analog converter which can be considered to represent a effective impedance coupled in parallel with emitter resistor R 11 . In this way stored digital threshold values were converted to analog values for coupling to the emitter of the current source transistor to provide individual sensor specific detection threshold values. 
   Block  400  of  FIG. 2  shows an inventive arrangement which facilitates varying detection threshold levels by selectably controlling signals added at the emitter of current source transistor Q 3 . Furthermore, because the sensor detection threshold can be controlled in accordance with the display color rather than the spatial position of the raster sensor, color specific threshold values are controllably selected by the colored video marker blocks M generated during automated adjustment. 
   Operation of block  400  is as follows. Part of a digital convergence system generates and positions within the display raster video marker blocks M to illuminate each sensor for each of the projection display colors. In block  400  exemplary red marker M video signal Rv from the digital convergence system is coupled via a potential divider formed by resistor R 16  to the base of transistor Q 7  with resistor R 17  coupled to ground. The emitter of transistor Q 7  is coupled to ground via a resistor R 18  and transistor Q 7  is arranged as the current source portion of a cascode amplifier with transistor Q 8 . The base of transistor Q 8  is supplied via resistor R 22  from a potential divider, coupled between a positive supply and ground and formed by resistors R 20  and R 21 . Transistor Q 8  forms an amplified signal ( 402 ) across resistor R 19  which is connected from the collector to an isolated positive supply associated with the red video amplifier U 2 . The junction of transistor Q 7  collector and transistor Q 8  emitter is also coupled via a series connected resistor R 23  to the junction of a capacitor C 5 , which is connected to a 3.3 volt positive supply, and a further resistor R 25  which is coupled to the base of a PNP transistor Q 6 . The base of transistor Q 6  is also connected to the positive supply via resistor R 25 . Transistor Q 6  is a saturating switch with the emitter connected to the positive supply and the collector sourcing current Ir via resistor R 15  to the emitter of reference current source transistor Q 3 . 
   Operation of the red marker signal amplifier is as follows. Cascode Transistors Q 7 , Q 8 , Q 10 , Q 11  and associated circuitry are configured as cascode video drivers with radio frequency filtering as discussed in U.S. Pat. No. 5,969,762 titled Video Signal Driver Including A Cascode Transistor which is hereby incorporated by reference. The cascode amplifier formed by transistors Q 7  and Q 8  has a voltage gain of approximately 2 and forms an inverted signal  402  which is coupled via amplifier U 2  to the red CRT as red marker block signal M, Rvout ( 408 ). 
   The actual amplitude of input signal Rv is determined by a 4 bit digital word hence red marker block signal Rv can have amplitude values in a range from 0.0 volts to 1.6 volts with a first step at zero volts and the 15 remaining values arranged evenly in the range 0.6 to 1.6 volts. During time interval t0.0-t0.5 mille seconds, as depicted in  FIG. 3A , red marker video signal Rv is at zero volts and transistor Q 7  provides no current to transistor Q 8 . The emitter of transistor Q 8  assumes a potential of approximately 3.3V due to a resistive path via resistors R 23 , R 24  and R 25 . In addition capacitor C 5  is discharged to zero volts via resistors R 23 , R 24  and R 25 . For Example, when an exemplary red marker signal is input having a step size of Vr=0.8 volts, 0.72 volts drives the base of transistor Q 7 , about 0.12 volts appears across resistor R 18 . This voltage results in approximately 5.3 mille Amperes flowing in resistor R 18  and charging capacitor C 5  through resistor R 23 . When capacitor C 5  has charged such that the emitter of transistor Q 8  reaches a potential of about 1.65 volts, transistor Q 8  turns on clamping further charging of capacitor C 5  and diverting the majority of the 5.3 mille Amperes current to resistor R 19 . This clamping point is determined by the base bias of 2.25V at transistor Q 8  base due the divider resistors R 20  and R 21 . A small fraction of the 5.3 mille Amperes current flows through resistor R 24  and provides base bias to transistor Q 6 . PNP transistor Q 6  saturates to near the supply voltage of +3.3 volts and conducts current Ir determined by the value of resistor R 15 . 
   The video marker image M is made up of short, aligned, lighted segments comprising a number of adjacent scan lines. When the marker video pulses end, transistors Q 7  and Q 8  turn off and capacitor C 5  slowly discharges through resistor R 24  into the base of transistor Q 6 . However, transistor Q 6  remains on for a time long enough to minimize additional capacitor charging from adjacent successive scan lines. This is necessary to limit a loss of contrast, or video amplitude, at the rising edge of the video pulse on the remaining lighted lines. Such a loss can interfere with accurate edge detection as the lighted area is moved across a light sensor. Only the first line of the lighted area M delivers full charging energy to capacitor C 5  and thus the marker has a loss in contrast and hence this area of the lighted marker is unused by the automation system. 
   Transistor Q 6  current Ir adds to the current Ig flowing in resistor R 11  and flows through transistor Q 3  to form current Iref. The sensor current Isen, due to marker M illuminating the sensor, must exceed the increased current Iref in order to deprive transistor Q 1  of base bias current Isw and cause the transistor Q 1  to switch off thereby indicating a lit sensor. Thus, the threshold for detection of red marker M images detected by detector transistor Q 10  is increased by the summation of currents Ir and Ig. 
   Operation of the blue marker signal amplifier comprising transistors Q 9 , Q 10  and Q 11  and blue video amplifier  407  is identical to that of the red amplifier with the exception that resistor R 14 , from the collector of transistor Q 9 , sources a current Ib with a magnitude approximately four times that generated responsive to the red marker video signal. 
   In the absence of both red and blue video signals Rv and By no additional current is summed at the emitter of transistor Q 3  and current Iref is substantially equal to Ig, the green detector threshold value. 
     FIGS. 3A-G  show various waveforms helpful in understanding the operation of the inventive arrangements of  FIG. 2 . Red marker video signal  401 , Rv, is depicted in  FIG. 3A . Red signal Rv, is divided by resistors R 16  and R 17  resulting in about 91% signal amplitude being coupled the base of transistor Q 7 . At the emitter of transistor Q 7  and across resistor R 18  the divided Rv signal appears minus with one base emitter diode drop producing a current in resistor R 18 . This current also flows through transistors Q 7  and Q 8  and resistor R 19  causing a voltage across resistor R 19  approximately twice that across resistor R 18 . This voltage, Rvout, drives red video inverting amplifier  406  and the red cathode ray tube (CRT). 
   The voltage at the junction of the transistor Q 7  collector and the emitter of transistor Q 8 , Vrcd, (V red color detect) is shown in  FIG. 3B . During time interval t0.0-t0.5 mille seconds, red marker video signal Rv is at zero volts, and voltage Vrcd is at 3.3 volts or approaching 3.3 volts due to the discharge of capacitor C 5  through resistors R 24  and R 25  and the base emitter junction of transistor Q 6 . The base emitter junction of transistor Q 8  is reverse biased and transistor Q 7  is non conductive. At time interval t0.5-t1.5 mille seconds, red marker pulses of about one volt are coupled to transistor Q 7  which turns on causing the base-emitter junction of transistor Q 8  to conduct. With transistor Q 8  turned on voltage Vrcd is clamped at about 1.65 volts, one base emitter diode drop below a voltage of 2.25 volts determined by divider resistors R 20  and R 21 . Voltage Vrcd is applied via resistor R 23  and charges capacitor C 5  away from the supply voltage to a voltage of, 3.3 volts minus 1.65 volts. This capacitor voltage is coupled via resistor R 24  to the base of PNP switching transistor Q 6  causing it to conduct and saturate such that the collector voltage is substantially at the supply voltage of 3.3 volts, shown as voltage Vreddet, (V red detected) in  FIG. 3C . 
     FIG. 3D  shows threshold current Iref from the collector of current source transistor Q 3 . As explained previously current Iref is determined by the sum of currents flowing in resistors R 11 , Ig; R 15 , Ir, and R 14 , Ib. A green threshold current Ig is always present and determines threshold current Iref for green image measurements. Red and blue threshold currents Ir or Ib respectively are added to current Ig by the switching action of transistors Q 6  or Q 9  which are driven by respective red and blue marker video signals, Vr, Vb. 
   Threshold current Iref is shown  FIG. 3D  and during time interval t0.0-t0.5 mine seconds is initially equal to Ig. At time interval t0.5 mille seconds a red video signal is generated and turns on transistor Q 6  and increases threshold current Iref to by red threshold current Ir.  FIG. 3E  shows current Isen which is determined by photo induced current in any of light sensors S 1  . . . S 8 . The sensor signal is amplified and converted to a voltage by amplifier U 1  and AC coupled via capacitor C 3  to appear across resistor R 6 . The base current driving light detecting switch transistor Q 1 , Isw, is shown in  FIG. 3F . Base current Isw is the sum of Iref and Isen. In  FIG. 3E  at about 1 mine second a marker M illuminates a sensor and current Isen momentarily exceeds threshold current Iref which causes current Isw to go to zero and turnoff transistor Q 1 . Current Iref then flows via resistor R 6  to charge capacitor C 3 . Positive feedback is used to slow the charging of capacitor C 3 . The marker light pulse is effectively stretched by biasing changes at the base of transistor Q 3  which reduces threshold currents Ig, Ir and Ib by about ⅓ thereby providing detector hysteresis. After about 4 mine seconds a second sensor is lit and detected due to a green marker image. Note that the voltage Vreddet of  FIG. 3C  has returned to its initial level, the value of current Iref of  FIG. 3D  has returned to its initial level and that during light pulse M current Iref is decreased by ⅓.  FIG. 3G , shows the light detection pulse V 202  that is supplied to the microcomputer to facilitate automatic adjustment.