Abstract:
The present invention discloses a magnetic field sensing device that utilizes a single coil for calibrating the response of the sensor to compensate for temperature dependent sensitivity drift and also for resetting the magnetic field sensor in order to eliminate hysteresis. The single coil configuration is advantageous since it reduces the size of the sensor chip by decreasing the number of contact pads on the chip and also because it wastes less space, which permits an increase in the density of the magnetoresistive elements on the sensor chip.

Description:
CROSS-REFERENCE TO A RELATED APPLICATION 
     This application is a 35 U.S.C. §371 national phase application of PCT/CN2012/082015, filed on Sep. 26, 2012, which claims priority to a Chinese Patent Application No. CN 201110356226, filed on Aug. 30, 2011, incorporated herein by reference in its entirety. 
     FIELD OF THE INVENTION 
     This invention relates to a magnetic field sensing device. 
     BACKGROUND OF THE INVENTION 
     Magnetic sensors are widely used in modern systems to measure or detect physical parameters including but not limited to magnetic field strength, current, position, motion, orientation, and so forth. There are many different types of sensors in the prior art for measuring magnetic field, but these sensors have limitations that are well known in the art, such as, excessive size, inadequate sensitivity and/or dynamic range, cost, reliability and other factors. 
     Hence, there is a need for improved magnetic sensors, especially sensors that can be easily integrated with semiconductor devices and integrated circuits and manufacturing methods thereof. 
     Magnetic tunnel junction (MTJ) sensors have the advantages of high sensitivity, small size, low cost, and low power consumption. Although MTJ devices are compatible with standard semiconductor fabrication processes, methods for building high performance MTJ linear magnetic field sensors have not been adequately developed. In particular, performance issues due to temperature dependence and hysteresis are not easy to control. 
     Magnetic field sensors may be constructed from a single magnetoresistive element, but in practice it is advantageous to configure several magnetoresistive elements into a Wheatstone bridge in order to eliminate offset, increase sensitivity, and provide some level of temperature compensation. Although bridge configurations do improve temperature compensation, the inherent temperature dependence of the magnetoresistance and magnetic properties of the sensor are not completely suppressed. For high accuracy, it is desirable to calibrate the sensitivity during operation, and an on-chip calibration coil that produces a known magnetic field along the sensitive direction of the sensor is often provided for this purpose. Calibration is often performed by periodically applying a low amplitude current pulse sequence to the calibration coil, which provides a known magnetic field pulse sequence from which the sensitivity of the magnetoresistive sensor may be determined during operation of the magnetometer. 
     Because magnetoresistive sensors are composed of ferromagnetic sensing elements, the sensor response is subject to nonlinearities, offset, and hysteresis due to the formation and motion of domain walls within the sensor elements or other components, such as magnetic shields and flux concentrators. To overcome this issue, high performance magnetoresistive sensors are often provided with another coil, orthogonal to the calibration coil that is used to periodically saturate the sensor elements and sweep out magnetic domains. This is referred to as a set/reset coil. 
     The presence of both the calibration and set/reset coils adds complexity to magnetoresistive sensor fabrication by increasing the number of process steps required to manufacture the sensor, and it increases the size of the sensor die by requiring more contact pads and to accommodate the geometrical constraints required to produce the orthogonal calibration and set/reset fields. 
     Magnetoresistive sensors without a calibration coil are possible. A disadvantage of this approach is the fact that the sensitivity of the sensor cannot be measured by electrical means. That is, if the magnetoresistive sensor does not have a calibration coil, the response of the sensor cannot be monitored and analyzed for sensitivity. Moreover, implementing a standard self-test in the sensor is cumbersome. 
     The magnetic field that is generated by a line current decreases inversely proportionally with the distance from the line. Power optimization indicates that the distance between the sensor and the calibration coil, and the distance between the sensor and the reset coil should be as small as possible. Ideally both coils should be located as close as possible to the sensor. This is however physically impossible. 
     SUMMARY OF THE INVENTION 
     The present invention provides a method for mass production of linear magnetoresistive sensor bridges using a simplified coil design. The disclosed sensor uses MTJ or giant magnetoresistive (GMR) elements combined with a single on-chip coil for the calibration and set/reset operations. The magnetometer uses a low unipolar or bipolar current pulse cycle for the calibration operation, and a large unipolar current pulse for the reset operation. 
     The present invention discloses a magnetic field sensing device, including magnetoresistive sensing elements, wherein the coercivity of said sensing elements is equal to the offset field of the sensing elements, a coil placed near said magnetoresistive sensing elements, which generates a magnetic field parallel to the sensing axis of said magnetoresistive elements, and a first current through the coil is used to reset the sensing elements while a second current is used to calibrate the response of the sensing elements. 
     Preferably, said first current through the coil is greater than said second current. 
     Preferably, said first and second currents are in the range of 1 to 10 mA. 
     Preferably, said coil is a single conductive layer. 
     Preferably the coil is a meander shape. 
     Alternatively, the coil is a spiral shape. 
     The sensor may be used as a compass. 
     In another implementation, the magnetic sensor includes a magnetic sensing element that has coercivity equal to its offset field is located close to a coil, and the coil generates a first magnetic field parallel to the sensing axis of the magnetoresistive sensor and a second magnetic field component perpendicular to the sensing axis of the magnetoresistive sensor, wherein the first magnetic field component is greater than the second magnetic field component, said first magnetic field component is sued for set/reset and calibration functions and said second magnetic field component is used to properly align domains at the edges of the magnetoresistive sensor elements, and further a first current through the coil is used for the set/reset function, and a second current is used for calibration of the magnetoresistive sensing element. 
     Preferably, said first current through the coil is greater than said second current. 
     Preferably, said first and second currents are in the range of 1 to 10 mA. 
     Preferably, the angle between the current direction and the long axis of the magnetoresistive sensing element is less than or equal to 22.5°. 
     Preferably, said coil is a single conductive layer. 
     Preferably the coil is a meander shape. 
     Alternatively, the coil is a spiral shape. 
     The sensor may be used as a compass. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         FIG. 1 —Schematic drawing of the configuration of s sensor element and coil. 
         FIG. 2 —Definition of magnetic sensor performance metrics. 
         FIG. 3 —Explanation of the reset operation. 
         FIG. 4 —Explanation of the calibration operation. 
         FIG. 5 —Edge domains in canted magnetoresistive element. 
         FIG. 6 —Edge domains in uncanted magnetoresistive element. 
         FIG. 7 —Schematic drawing of a meander coil geometry that may be used to decrease the size of the magnetometer chip. 
         FIG. 8 —A schematic drawing of the spiral coil geometry. 
     
    
    
     DETAILED DESCRIPTION OF EXEMPLARY EMBODIMENTS 
     The invention relates to an electronic device with a high accuracy magnetoresistive sensor to be used in low cost and possibly low power applications. Low-power sensors are particularly interesting for mobile electronic devices such as mobile telephones, watches, portable computers, or personal touch screen devices, etc. In particular, magnetoresistive sensors can be used to implement an electronic compass in order to provide a navigational reference with respect to the earth&#39;s magnetic field. 
       FIG. 1  illustrates the simplified concept of the sensing element and coil geometry. Here, a magnetoresistive sensor element  10  sits atop or beneath a conductor  11 , through which a current  12  is sourced. The current  12  produces a magnetic field, B(I)  13  in a direction perpendicular to the current flow. The sensor  10  and conductor  11  may optionally be set at an angle  14  so that the magnetic field  13 , is not perpendicular to the sensing direction  15  of the sensor  10 . 
       FIG. 2  depicts a transfer curve  20  for magnetoresistive sensors in order to define the coercivity (H c )  21  and offset (H offset )  22  parameters. The transfer curve  20  is a measure of sensor output voltage  23  as a function of applied magnetic field  24 . Ideally, sensing is performed on the arm of the transfer curve  20  that passes through the origin of the plot  25 . Then provided the sensor is never driven into saturation beyond point  26 , the sensor approximates linear response. This is an over simplification, as the sensor will drift with changes in temperature and lower values of field, but provided the sensor is periodically initialized, it can remain on portion  25  of the transfer curve. 
     A sensor can be operated in this low hysteresis mode if the following condition is met:
 
H c =H offset ,  (1)
 
and the devices is periodically saturated using a field along the sensing direction  15  that drives the transfer curve beyond point  27 .
 
     A simple initialization procedure is shown in  FIG. 3 . Here, a field value denoted as H reset    30  is applied to the sensor to cause it to go into saturation at a field greater than that associated with point  27  on the transfer curve. Upon removal of H reset    30 , the sensor follows path  31 - 32  and returns to operating point  25 . This simple reset procedure would likely be the most power efficient means for removing coercivity, but it may produce better results to use a bipolar pulse sequence, or a multi-shot unipolar pulse sequence, provided the last pulse always supplies a field that saturates the magnetoresistive sensor at field  30  or greater than field  30 . 
     After initialization, the device may be calibrated or self-tested during operation as illustrated in  FIG. 4 . Here, a small calibration pulse is applied through the current conductor to produce a small field H cal    40  collinearly with the sensing axis. The field produces a voltage change in the magnetoresistive sensor ΔV  41  in response to the known change in the applied magnetic field ΔH  42 , such that the sensitivity may be determined from
 
Sensitivity=Δ V/ΔH.   (2)
 
The calibration procedure may be accomplished using a pulse train at some specific frequency or shape such that it is possible to distinguish it from the background signal. The calibration can be performed periodically to remove temperature dependence of the magnetoresistive sensor elements. The pulse train can be unipolar or bipolar, it may be a single pulse, or it may be a continuous square wave or sinusoidal tone.
 
     It is often advantageous to rotate the sensor element  10  by angle α  14  with respect to the coil  11  as illustrated in  FIG. 1 . The reason for this is illustrated in  FIGS. 5 and 6 . 
       FIG. 5  shows the case where the sensor element  10  is rotated with respect to the coil  11  by angle α  14 . In this configuration, H reset    30  will have a component H edge    51  that is parallel to the edge of the sensor element  10 . In the presence of sufficiently large Hedge, the edge domains  51  are forced to align in the same direction, providing a well defined initial state for the magnetization of the magnetoresistive sensor  10 . When a first current in the coil is applied, a magnetic reset operation can be performed; when the second current in the coil is applied, a calibration operation is performed. The first current is greater than the second current, and the first and second currents are in the range of 1 to 10 mA. 
       FIG. 6  illustrates a possible edge domain arrangement for a sensor  10 —conductor  11  arrangement that does not produce a reset field component H edge    50  parallel to the sensor edge. In this case, there is no driving force to align domains at the edge of the sensor  51 , and it is possible for head-to-head domains to form at the edges  61 . This is a stochastic process, that makes the device unpredictable, and motion of the domains during operation can produce hysteresis. 
     The calibration may be corrected as follows:
 
 H   true   ≈H   cal Cos(α)  (3)
 
This provides better than 90% accuracy for angles as large as 22.5 degrees. Larger angles can be adjusted for the decrease in sensitivity resulting from the H edge    50  component, if needed. Alternatively, if the sensor is biased using on-chip magnets or in-stack biasing, the H edge  component present during calibration may not have any significant influence on the calibration.
 
     A preferred layout for the coil is shown in  FIG. 7 . The traditional layout is shown in  FIG. 8 . In the preferred layout, the coil is a meander pattern, with return leads  71  that run between sensor elements  10 . This arrangement permits the sensor elements to be more tightly packed than the conventional spiral geometry shown in  FIG. 8 . A potential issue with the meander coil geometry is high resistance. The resistance of the coil is given as: 
                       R   ⁡     (     L   ,     W   1     ,     W   2     ,     W   3     ,   t   ,   ρ     )       ≈       ρ   t     ⁡     [       L   ⁢           ⁢     N   ⁡     (       1     W   1       +     1     W   2         )         +       g   ⁡     (       2   ⁢           ⁢   N     -   1     )         W   3         ]         ⁢     
     ⁢   If           (   4   )                   g     W     3   ⁢                 ≈       L   ⁡     (       W   1     +     W   2       )           W   1     ⁢     W   2           ⁢     
     ⁢     Then   ⁢     :               (   5   )                 R   ⁡     (     L   ,     W   1     ,     W   2     ,     W   3     ,   t   ,   ρ     )       ≈         ρ   ⁢           ⁢   L   ⁢           ⁢   N     t     ⁢     (       1     W   1       +     1     W   2         )               (   6   )               
The field produced by the portion of the meander coil that runs atop or beneath the sensor elements is given by:
 
                       B   x     ⁡     (     x   ,   y     )       =         μ   0       4   ⁢           ⁢   π       ⁢     I   tW     ⁢     (               (     x   -     W   /   2       )     ⁢     {     ln   ⁡     [           (     x   -     W   /   2       )     2     +     y   2             (     x   -     W   /   2       )     2     +       (     y   +   t     )     2         ]       }       -                   (     x   +     W   /   2       )     ⁢     {     ln   ⁡     [           (     x   +     W   /   2       )     2     +     y   2             (     x   +     W   /   2       )     2     +       (     y   +   t     )     2         ]       }       +                 2   ⁢     (     y   +   t     )     ⁢     {       ATan   ⁡     [       x   +     W   /   2         y   +   t       ]       -     ATan   ⁡     [       x   -     W   /   2         y   +   t       ]         }       -               2   ⁢           ⁢   y   ⁢     {       ATan   ⁡     [       x   +     W   /   2       y     ]       -     ATan   ⁡     [       x   -     W   /   2       y     ]         }             )               (   7   )               
Here, “W” is the width of the conductor, “t” is the thickness of the conductor, “y” is the height above (or below the surface of the conductor), and “x” is a position along the sensing axis from the center of the conductor.
 
     Note also,
 
 I   reset   ≦V   max   /R ( L,W   1   ,W   2   ,W   3   ,t ,ρ)  (8)
 
Where the geometric parameters are defined in  FIG. 7 , ρ is the conductivity of the coil material, and V max  is the maximum possible voltage the magnetometer system can deliver.
 
     It is apparent that care must be taken such that H reset  can be achieved using a voltage that is less than V max . Although it is possible to use a switched capacitor scheme to achieve sufficient voltages, it is preferable to keep the voltages in the range of 5 V or smaller. The voltage constraint and coil resistance places restrictions on magnetoresistive element  10  and magnetometer design. They place an upper bound on the achievable H reset  and limit the size of the reset coil. 
     It will be apparent to those skilled in the art that various modifications can be made to the proposed invention without departing from the scope or spirit of the invention. Further, it is intended that the present invention cover modifications and variations of the present invention provided that such modifications and variations come within the scope of the appended claims and their equivalence.