Patent GB-650114-A (GB)
Title: Improvements in or relating to distance measuring devices utilising reflected wave energy
IPC: G01S13/32
Filed: 1947-12-24
Abstract: 650,114. Phase difference measuring. GUANELLA, G. Dec. 24, 1947, No. 34245. Convention date, Sept. 26, 1938. [Class 37] [Also in Groups XXXVIII and XL (c)] Relates to continuous-wave radar and similar wave-energy distance measuring systems in which a portion of the transmitter output is applied to a delay device which is adjusted so that the delay produced by the device is equal to the propagation time of the reflected wave, this condition being indicated quantitatively by combining the reflected wave with the delayed wave from the device. According to the invention, the transmitted signal consists of a complex wave of substantially constant mean energy content and comprising a plurality of components of different frequencies the indicating quantity having a magnitude proportional to the mean product of the reflected and delayed waves. The complex wave may comprise random noise components or it may be produced by frequency modulating a carrier and the wave may be radiated directly or amplitude modulated on to a highfrequency carrier. The invention is described as applied to radar systems, Figs. 4 and 5 (not shown, a system for locating faults in a cable, Fig. 6, and an altimeter utilizing compressional waves, Fig. 3, but the methods of ranging described are not dependent on the nature of the wave energy transmitted. The indicating quantity may be produced by forming the product of the reflected wave r1 and the delayed wave r2 in a modulator and applying the D.C. output to a voltmeter ; alternatively the two waves may be applied respectively to the two coils of a wattmeter or watt-hour meter. When the two waves are applied direct to the product-forming circuit, the magnitude of the indicating quantity G varies as in Fig. 1 where T1 is the propagation time of the reflected wave and T2 is the delay time of the delay device. In order to produce a null indication the waves r1 and r2 are subjected to phase shifts of p and q respectively where p and q are independent of frequency and the average product H of the resultant waves s1 and s2 then varies as shown in Fig. 2 when (p-q)=90 degrees. In either method the frequency of the waves r1 and r2 may be shifted by heterodyning with a local oscillation and in the latter method the necessary phase condition is obtained by providing phase quadrature local oscillations. In the second method, any deviation from the phase condition (p-q)=90 degrees causes a variation in the magnitude of the quantity H and this may be minimised by forming the difference and sum of waves r1 and r2 and applying the resultant waves (r1-r2) and (r1+ r2), through the phasing circuits to the product-forming circuit, a less satisfactory method is to combine the wave r2 with the difference wave (r1 -r2) or summation wave (r1+r2). In order to measure the ranges of a number of objects located at different distances, the oscillation periods of the components of the complex wave should be small compared with the difference in the propagation times for the different objects and in order to maintain the mean energy content of the complex wave substantially constant, the components should not be harmonically related. Directional transmission and reception may be employed to minimise direct reception of the transmitted signal and any residual coupling may be neutralized by injecting a portion of the transmitter output into the receiver to oppose the directly received signal but it is shown that the effects of such coupling on the indicating quantity is negligible if the oscillation periods of the components of the complex wave are small compared to the propagation and delay times. The amplitude of the reflected wave may be increased by employing a reflecting mirror or responder at the reflecting object. In the F.M. radar shown in Fig. 4, the frequency of an oscillator 94 is varied in a sawtooth manner by the relaxation oscillator 92 and reactance valve N and the amplified output r0 from G4 is applied to U1 to amplitude modulate a high-frequency carrier from the oscillator G5, the output from U1 being radiated from the transmitter aerial E1. The reflected signal received at E2 is demodulated at U2 and the demodulated output r1 applied to a transformer S3 together with a delayed wave r2 obtained by applying the wave r0 to a delay line Z4 which has an adjustable output tapping. The outputs from S3 comprising sum and difference waves (r1+r2) and (r1-r2) are applied to frequency changers U4 and U5 respectively together with the phase quadrature outputs from the local oscillator G6 and the amplified beat frequencies s1 and s2 from U4 and U5 are fed to a balanced modulator M4 to produce a D.C. output H (Fig. 2) which is applied to the voltmeter J. The tapping on the delay line Z4 is automatically adjusted by applying the modulator output H to a polarized relay D4 controlling a motor x which moves the tapping. In order to maintain the amplitude of the signals r1 and r2 equal, the signals are rectified at Q1 and Q2 and the difference e of the rectified outputs is applied to control the gain of amplifier A3. Fig. 5 (not shown), illustrates a radar system transmitting a complex wave in which the coupling between the transmitting and receiving aerials is reduced by separating the transmitter and receiver by a substantial distance, a portion of the transmitter output being transmitted to the delay line at the receiver via a separate radio link. Alternatively the radio link may be omitted and the transmitting and receiving aerials located so that the receiving aerial picks up the transmitted wave r0 and the reflected wave r1 both of the two waves being applied to the product forming circuit over two paths one including a 90 degrees phase shifter and the other the delay line. In such a case the output s1 from the phase shifter will contain a component which is only slightly delayed by the direct transmission and the output s2 from the delay line will contain a component which is delayed by the sum of the retardation time and the propagation time but these two components will have no effect on the average value of the product. Fig. 6 shows an embodiment for locating faults on a two-wire cable B1, B2. A suitable band r of the frequency spectrum of the noise potential generated at G1 is selected by the filter F and amplified at A1, the resultant wave r being applied to the cable via the transformer S6 and also to the adjustable delay line 36. The reflected wave r1 produced by a fault at R1 is coupled via the transformer S7 and amplifier A3 to the moving coil S8 of a wattmeter J6, the output r2 from the delay line being applied via network P6 and switch D6 (upper position) to the fixed coil S9. When the arm of switch D7 is on the left-hand contact as shown, the network P6 acts as an attenuator and the wattmeter deflection varies with the setting of the delay line as shown in Fig. 1 but when the arm is on the right-hand contact, the network P6 acts as a 90 degrees phase shifter and the wattmeter deflection varies as in Fig. 2. By changing the switch D6 to its lower position, the reflected signal r1 is applied to both the fixed and moving coils of the wattmeter which then indicates the mean square value of the signal. Since the propagation time of a cable is usually frequency dependent the transmission characteristics of the delay line Z6 should simulate the cable under test. Compressional wave system, Fig. 3. The complex transmitted wave r1 is produced by amplifying at A1 the noise potential generated in an oscillator G1 and the wave r0 is applied to an electro-acoustic transducer E1 and to a magnetic-tape delay device Z3 comprising a moving steel tape, recorder K1, adjustable pick-off K2 and eraser K3. The delayed wave r2 from Z3 and the amplified output wave r1 from the receiving transducer E2 are applied to a ring modulator M3 via R.C. phase delay and phase advance networks P2 and P1 and when the time constants of the two networks are equal the difference of the phase shifts produced by P1 and P2 is equal to 90 degrees for any frequency so that the D.C. output H from M3 applied to the voltmeter J is as shown in Fig. 2. When used as an aircraft altimeter, the noise of the engine and propeller may be used as the transmitted wave. A similar system may be employed in geological surveys for locating subterranean or subaqueous strata.