Patent GB-1264165-A (GB)
IPC: H02P27/04
Filed: 1969-04-17
Abstract: 1,264,165. Control of A.C. motors. SIEMENS A.G. 17 April, 1969 [18 April, 1968 (2)], No. 19763/69. Heading H2J. [Also in Divisions G1 and G3]  An arrangement for producing a signal proportional to the square of the magnitude of a rotating vector parameter of a three -phase electrical system comprises means for producing signals related to at least the voltages in at least two phases of the system, means for producing, in dependence on said signals, further signals related to instantaneous values of components of said rotating vector parameter, multipliers coupled to the further signals for forming a plurality of functions which contain the square of each of said instantaneous values and the produce of at least one distinct pair thereof, and summation means coupled to the outputs of the multipliers, the output of the summation means being the desired square of the magnitude of said system. The invention is used to derive the actual values of flux #, torque M, slip speed # 2  and rotational speed # of an asynchronous motor from measurements of the voltages and currents in at least two stator windings. The speed # may be derived or measured by a three phase tachogenerator, the output of which constitutes the electrical system of the invention. Fig. 4 shows the arrangement for deriving #<SP>2</SP> from which # is produced by a root function device not shown. Voltage transformers 18, 19 produce phase voltage signals, from which instantaneous line voltages U R  and Us are derived by the combining arrangement shown, devices 20 ... 23 being amplifiers whose relative gains are indicated in the symbol. Current transformers 24, 25 in series with two of the stator windings of motor 4 each have a resistor and an inductor across their secondary windings, from which are produced signals I R , I S  proportional to the instantaneous current and - dI R /dt, -dIs/dt proportional to its rate of change. These three signals for each phase are added and integrated at 38, 39, the integrators having negative feed-back amplifiers 42, 43 to correct zero drift. It is shown that the outputs of the integrators are the instantaneous values of the fluxes #R, #S which are the "components of the rotating vector parameter" in this ease. These are applied to the arrangement 17 in which each is squared and also the terms are multiplied by each other to produce the sum #R<SP>2</SP> + #R.#S + #S<SP>2</SP>, which it is shown is equal to #<SP>2</SP>. Alternative arrangements of multipliers within 17 are described (Figs. 4a, 4b, not shown), in one of which a parabolic amplifier is used for obtaining the square, instead of the two-input multipliers shown. When the square root is taken the output is a unidirectional voltage proportional to the rotating vector, in this case, flux. In Fig. 5 (not shown) signals representing torque, speed and slip are derived. Stator flux signals #R and #S from 16 of Fig. 4 are added to stator current signals I R  and Is with appropriate weighting to give (it is stated) rotor flux signals; these, multiplied by I R , Is and added give a signal (M) for torque. To avoid instability in a control system around the stalling point, this torque signal is "linearized" by dividing it by the square of the rotor flux vector (at 67) and multiplying the quotient by the square of the stator flux vector (at 68). The result (M L ) is the required torque signal. The output of the divider after amplification (69), is the slip speed signal (it is stated) and this subtracted from the speed of the rotating field gives the actual speed signal. These speeds signals are only correct for steady state conditions, but in Fig. 7 (not shown) a method is shown, using signals produced in 16 of Fig. 4 for producing dynamic signals for the rotor speed and slip. Alternatively, the rotor speed can be measured directly by a three phase A.C. tachogenerator whose output is converted to a unidirectional signal proportional to instantaneous speed by the arrangement of the invention. One method is shown in Fig. 15, in which RST are the output voltages of the tachogenerator, 132, 133 are voltage transformers and 134, 135 are amplifiers having the relative gains indicated, from which line voltage U R  is derived, which is squared in a function generator 118. The phase voltage U ST  is also squared, at 121, and U ST 2 is equal to (Us - U T )<SP>2</SP>. This is added to UR<SP>2</SP> multiplied by 3 and the square root of the result taken at 110 to give the required speed signal. The mathematical basis is given in the specification. Alternative arrangements of multipliers and function generators, for use when the neutral point is available, are described with respect to Figs. 12, 13, 14 (not shown). Fig. 8 (not shown) illustrates further details of one of the arrangements 17 of Fig. 4. Figs. 9 and 10 (not shown) illustrate arrangements similar to those of Figs. 4 and 5 but which measure voltages and currents in all three phases. Fig. 1 shows how the derived "actual values" (which appear on terminals 6 ... 9) are used to control the motor 4. The motor is supplied from a source N via a frequency changer 5 whose output frequency is controlled by a regulating unit 14 from a controller 13 responsive to the difference between actual torque M or slip speed # 2  and a reference M*, which is produced by a speed controller 12 responsive to the difference between actual rotor speed # and a reference value #*. The magnitude of the output of 5 is controlled by a regulator 11 from an amplifier 10 responsive to the difference between flux # and a reference #* or between a rotating voltage vector and a reference (not shown).