zilongwang/ReadingBank huggingface dataset:
Attachment 2 Objectives In planning the implementation of IMT, the following objectives are desirable: – to ensure that frequency arrangements for the implementation of IMT have longevity, yet allow for the evolution of technology; – to facilitate the deployment of IMT, subject to market considerations and to facilitate the development and growth of IMT; – to minimize the impact on other systems and services within, and adjacent to, the bands identified for IMT; – to facilitate worldwide roaming of IMT terminals; – to integrate efficiently the terrestrial and satellite components of IMT; – to optimize the efficiency of spectrum utilization within the bands identified for IMT; – to enable the possibility of competition; – to facilitate the deployment and use of IMT, including fixed and other special applications in developing countries and in sparsely populated areas; – to accommodate various types of traffic and traffic mixes; – to facilitate the continuing worldwide development of equipment standards; – to facilitate access to services globally within the framework of IMT; – to minimize terminal costs, size and power consumption, where appropriate and consistent with other requirements; – to facilitate the evolution of pre-IMT-2000 systems to any of the IMT terrestrial radio interfaces and to facilitate the ongoing evolution of the IMT systems themselves; – to afford flexibility to administrations, as the identification of several bands for IMT allows administrations to choose the best band or parts of bands for their circumstances; – to facilitate determination, at a national level, of how much spectrum to make available for IMT from within the identified bands; – to facilitate determination of the timing of availability and use of the identified for IMT, in order to meet particular user demand and other national considerations; – to facilitate development of transition tailored to the evolution of existing systems; – to have the ability for the identified bands, based on national utilization plans, to be used by all services having allocations in those bands. The following guiding principles have been applied in determining frequency arrangements: – harmonization; – technical aspects; – spectrum efficiency.
2 (continued) IEEE Std (Clause 17, commonly known as 802.11b) IEEE Std 802.11-2012 (Clause 18, commonly known as 802.11a(1)) IEEE Std (Clause 19, commonly known as 802.11g(1)) IEEE Std (Clause 18, Annex D and Annex E, commonly known as 802.11j) IEEE Std 802.11-2012 (Clause 20, commonly known as 802.11n) IEEE Std ETSI EN 300 328 ETSI EN 301 893 ARIB (1) ETSI EN 302 567 Data rate 1, 2, 5.5 and 11 Mbit/s 6, 9, 12, 18, 24, 36, 48 and 54 Mbit/s 1, 2, 5.5, 6, 9, 11, 12, 18, 22, 24, 33, 36, 48 and 54 Mbit/s 3, 4.5, 6, 9, 12, 18, 24 and 27 Mbit/s for 10 MHz channel spacing 6, 9, 12, 18, 24, 36, 48 and 54 Mbit/s for 20 MHz channel spacing From 6.5 to 288.9 Mbit/s for 20 MHz channel spacing From 6 to 600 Mbit/s for 40 MHz channel spacing From 6.5 to 693.3 Mbit/s for 20 MHz channel spacing From 13.5 to 1 600 Mbit/s for 40 MHz channel spacing From 29.3 to 3 466.7 Mbit/s for 80 MHz channel spacing From 58.5 to 6 933.3 Mbit/s for 160 MHz and 80+80 MHz channel spacing 6, 9, 12, 18, 27, 36 and 54 Mbit/s HiSWANa
HiSWANa, TABLE 2 (end) Characteristics IEEE Std (Clause 17, commonly known as 802.11b) IEEE Std 802.11-2012 (Clause 18, commonly known as 802.11a(1)) IEEE Std 802.11-2012 (Clause 19, commonly known as 802.11g(1)) IEEE Std 802.11-2012 (Clause 19, Annex D and Annex E, commonly known as 802.11j) IEEE Std 802.11-2012 (Clause 20, commonly known as 802.11n) IEEE P802.11ac IEEE Std 802.11ad-2012 EN 300 328 EN 301 893 ARIB ETSI EN 302 567 Transmitter Interference mitigation LBT LBT/DFS/ TPC LBT LBT/DFS/TPC LBT DAA/LBT, DAA/non-LBT, MU LBT/DFS/TPC LBT Receiver Sensitivity Listed in Standard (1) Parameters for the physical are common between IEEE 802.11a and ARIB HiSWANa. (2) See 802.11j-2004 and JAPAN MIC ordinance for Regulating Radio Equipment, Articles 49-20 and 49-21. (3) DFS rules apply in the 5 250-5 350 and 5 470-5 725 MHz bands in many administrations and administrations must be consulted. (4) Pursuant to Resolution 229 (Rev.WRC-12), operation in the 5 150-5 250 MHz band is limited to indoor use.
TABLE 1 (continued) Parameter Units System 1 System 2 System 3 System 4 System 5 System 6 System 7 System 8 System 9 System 10 Antenna maximum gain dBi 34.5, transmit 33.5, receive 32.4-34.2, transmit 33.8-40.9, receive 38.9, transmit 38.2, receive 32.5 38.5 34 35 34.5 30 35-40 Antenna elevation beamwidth degrees 3.6 shaped to 44 3.63-5.61, transmit 2.02-8.79, receive 1.3 4.5 shaped to 40 2 3.75 (cosecant squared) 3.75 (cosecant squared) 3.7 shaped to 44 (cosecant squared) 20 (sinc) 3.75 Antenna azimuthal beamwidth degrees 1.2 1.4 3.2 3.0 2.2 1.2 1.3 1.2 2 2 Antenna horizontal scan characteristics rpm 360° mechanical at 5 rpm 360° mechanical at 5 rpm 360° mechanical at 6 rpm for long and 12 rpm for short range 360° mechanical at 6, 12 or 15 rpm 5 6 5 360° mechanical at 5 rpm 360° Electronically at variable rate 360° at 12-15 rpm or Sector scan at variable rate Antenna vertical scan characteristics degrees Not applicable –7 to +30 in 12.8 or 13.7 ms –1 to +19 in 73.5 ms Not applicable −6 to +20 −4 to +20 −4 to +20 Not applicable Not applicable Not applicable Receiver IF bandwidth kHz 780 690 4 400 to 6 400 1 200 1 250 625 720 to 880 (log) 1 080 to 1 320 (MTI) 270 to 330 (20 series log) 360 to 480 (20 series MTI) 540 to 660 (60 series log) 720 to 880 (60 series MTI) 1 200 Up to 10 000 2 000 Receiver noise figure dB 2 2 4.7 3.5 2.6 4.25 9 3.2 3 3
resources required (in days or months as applicable). About 10-20 activities is usually appropriate. The following table may be useful but an alternative format is acceptable; Activity Description Deliverable(s) expected Resources Required (Estimate) Development of feature X This will involve … and … that … Feature X ready for customer trials 3 engineers for 3 months plus 10 days from … Implement Process Y Note: Applicants may wish to insert a Gantt chart into this section to help illustrate the plan but that should not replace a detailed description of the activities to be carried out 4 Project Team Describe the project team (including levels of experience); Do you plan to use external consultants and what is their expected role? If there are team members yet to be identified, explain the strategy to find them and the expected timeframe? will the team be located? What are the skill/capability gaps in the team and what is the strategy to build capability?
– Multiplexing/demultiplexing of higher layer PDUs – Multiplexing/demultiplexing of multiple TBFs on the same PDTCH. – Scheduling of RLC/MAC data and control PDUs delivered to the physical channel on a shared channel – Splitting/recombining RLC/MAC PDUs onto/from several shared logical channels. RLC operates in Acknowledge mode (AM) or UnAcknowledged mode (UM). Functions include: – Segmentation of layer PDUs into RLC data blocks – Concatenation of layer PDUs into RLC data blocks – Padding to fill out RLC data – Reassembly of RLC data blocks into upper layer PDU – In-sequence delivery of upper layer PDUs – Link Adaptation – Ciphering and deciphering in Iu Mode – Sequence number check to detect lost RLC blocks. For Iu mode of operation, RLC can also operate in Transparent Mode for carrying spectrally efficient VoIP. In addition to the RLC provides the following functions when operating in ACK mode: – Backward (BEC) procedure enabling the selective retransmission of RLC data blocks. – Discard of RLC SDUs not yet segmented into RLC PDUs, according to the requirements of the associated . 4.3.7. RRC layer design Radio Resource Control (RRC) layer design for SRI- is based on ETSI GERAN Iu mode RRC specifications () specifications with satellite specific optimizations to cater to long delay environments and achieve better spectral efficiency. RRC state model is based on RRC states defined in TS and is illustrated in Fig. . RRC functions include: – Assignment, reconfiguration, and release of radio resources for the RRC connection – Establishment, reconfiguration, and release of – Release of signalling connections – Paging – Routing of higher layer PDUs – Control of requested QoS – Control of – Integrity – Support for
TABLE 2 (end) Characteristics Units System 1 5 MHz System 2 13 MHz System 3 25 MHz System 4 42 MHz Transmitter emission bandwidth 3 dB 20 dB kHz 26 58 54 70 105 150 128 170 Suppression of harmonics Yes (1) Range depends on a number of environmental factors: external noise, significant wave height, current speed, location of radar (such as proximity to water, nearby obstructions), and the operating frequency. (2) Range reduces significantly during night time. (3) While the sweep bandwidth is adjustable (higher bandwidth produces higher resolution data), the systems are normally operated at the typical sweep bandwidths specified due to limited available bandwidth, and the need to coexist with other radio systems. (4) Specifies the frequency for optimum performance from a scientific perspective. Entire frequency range not needed for operations. (5) RBW stands for resolution bandwidth. TABLE 3 Characteristics of generic oceanographic frequency modulated continuous wave (FMCW) radars Characteristics System 5 8 MHz System 6 12 MHz System 7 16 MHz System 8 25 MHz System 9 42 MHz Function Very long-range oceanographic measurements Long range oceanographic measurements Standard oceanographic measurements High-resolution oceanographic measurements Best resolution short range measurements Maximum operational (measurement) range km 150-300 (average during daytime)(1) 100-150 (average during daytime)(1) 50-100 (average during daytime)(1) 30-60 (average during daytime)(1) 10-20 (average during daytime)(1) Range resolution km 3-12 1-3 1-3 High resolution mode: 0.5 km 0.5-2 High resolution mode: 0.25 km 0.15-0.5 Sweep bandwidth kHz 50-12.5 150-50 300-50 600-75 300-1 000
TABLE 3 (continued) Characteristics Units System 5 8 MHz System 6 12 MHz System 7 16 MHz System 8 25 MHz System 9 42 MHz Frequency range MHz 6-9 11-14 14-18 24-27 40-44 Average power into antenna (= peak power) W 30 7 per antenna Pulse widths No pulse Maximum duty cycle Continuous wave rise/fall time Continuous wave Transmitter tuning method Digital (DDS) Receiver tuning method Digital (DDS) Output device Solid state, bipolar (Class AB operation) Transmitter stability ppm 0.1/year Receiver stability ppm 0.1/year Transmit antenna pattern type Directional > 90% energy within ±60° beamwidth Transmit antenna type 4 vertical monopole rectangular array 0.5 × 0.15 wavelength Antenna polarization Vertical Antenna main beam gain dBi 5 to 8 Transmit antenna elevation beamwidth degrees 25 to 35 Transmit antenna azimuthal beamwidth degrees 120
S-eNodeB Satellite eNodeB in the SAT-OFDM S1AP S1 application protocol SAT-eNB Satellite eNodeB SDU Service data unit S-GW Serving gateway SC-FDMA Single carrier frequency division multiple access SCH Synchronization signal SFBC block coding SI System information SIR Signal to interference ratio SN Sequence number SNR Signal to noise ratio SRS Sounding reference symbol SSS Secondary synchronization channel STC coding TA Time advance TB Transport TDM Time division multiplexing TF Transport format TM Transparent mode TMSI Temporary mobile subscriber identity TS Technical specification TTA Korean telecommunication technology association TTI Transmission time interval Tx Transmitter UCI Uplink control information UE User equipment UL Uplink UL-SCH Uplink shared channel UM Unacknowledged mode UTC Coordinated universal time VARQ Virtual HARQ VoIP Voice over Internet protocol X2AP X2 Application Protocol
52 subcarriers Forward error correction Convolutional coding, rate = 1/2, 3/4, 2/3 Convolutional coding, rate = 1/2, 3/4 Convolutional coding, rate = 1/2, 3/4 Convolutional coding, rate = 1/2, 3/4 Data transmission rate 3 Mbit/s, 4.5 Mbit/s, 6 Mbit/s, 9 Mbit/s, 12 Mbit/s, 18 Mbit/s, 24Mbit/s, 27Mbit/s 3, 4.5, 6, 9, 12, 18, 24 and 27 Mbit/s for 10 MHz channel spacing 6, 9, 12, 18, 24, 36, 48 and 54 Mbit/s for 20 MHz channel spacing 3 Mbit/s, 4.5 Mbit/s, 6 Mbit/s, 9 Mbit/s, 12 Mbit/s, 18 Mbit/s 3, 4.5, 6, 9, 12, 18 Mbit/s, Option: 24, 27 Mbit/s Media access control CSMA/CA CSMA/CA CSMA/CA CSMA/CA, Option: Time Slot based CSMA/CA Duplex method TDD TDD TDD TDD
The multipaths arrive at the terminal uniformly from all horizontal directions. Figures 4 and 5 show the typical rooms considered, rectangular and circular, respectively. 3 System model 4 Rectangular-shaped room layout FIGURE 5 Circular-shaped room layout 10.2.1 Probability density function of received power The PDF of received rp at the mobile terminal is given by the Nakagami-Rice distribution as follows. (19) where I0(x) is the first kind 0th-order modified Bessel function and K represents the following Kfactor. (20) where: (21) Here eDirect(x) represents the complex envelop of the direct path and es(x) represents the complex envelop of multipaths without moving objects around the MT at the position of x, which depends on only the surrounding static environment; their values do not depend on time t. Pm represents total multipath power. SShape is a constant value determined by the room’s shape and dimensions. 10.2.2 Autocorrelation function of received signal level The autocorrelation function R(t) of the received complex signal level with time difference t is given as follows: (22) where: (23) FIGURE
16 Resulting spatial correlation Envelope correlation coefficient versus the normalized distance = d/λ for the two-cluster case shown in Fig. 15. 3 Effect of the correlation coefficients on MIMO capacity For Rayleigh fading channels, the ergodic MIMO capacity without channel knowledge at the transmitter is: (24) where: nR and nT: number of receiver and transmitter antennas, respectively p: average received power per antenna σ2: noise power at each receive antenna : nR × nR identity matrix ()H and det(): Hermitian and determinant operation, respectively Hw: matrix elements are independent identically-distributed complex Gaussian Random variables with zero mean and unit variance ()½: Hermitian square root of a matrix. The matrices RR and RT determine the spatial correlations between the receivers and the transmitters, respectively, where the channel matrix H is defined by , and are positive definite Hermitian matrices, and finally they are assumed to be normalized such that [RR] j,j for j = 1, K, nR and [RT] i,i for i = 1, K, nT. By assuming that RR and RT have full rank and nR = nT = n, then at high S/N (p/2) the capacity can be approximated as: (25) If we denote the eigenvalues of RR by λi, i = 1, K, n, then . From the arithmetic meangeometric mean inequality: (26) Since , it follows that log2 det(RR) 0, and is zero only if all eigenvalues of RR are equal, i.e. RR = In. Thus, the correlation determines the MIMO capacity and the loss in the ergodic capacity at high S/N is given by (log2 det(RR) + log2 det(RT)) bit/s/Hz. Figure 17 illustrates the effect of spatial correlations on the ergodic capacity of a MIMO channel with nR = nT = 2. In the figure RT = I2, is assumed. The receiver correlation matrix is chosen according to: (27) where ρR denotes the spatial correlation between the receive antennas. 17 Ergodic capacity with low and high receive correlation
Definition of nonspec Defining spec and trans as the fraction of the coherent power impinging on F that is reflected as specular (coherent) reflection and transmitted through the facet, respectively, a consistent model of the complete scatter process might be expected to conserve energy, giving: (9) Unfortunately, our semi-empirical model is not consistent, and different assumptions are made for each mechanism: – spec: the most theoretically based model is that for specular scatter. For a smooth facet, the reflected power is determined by the Fresnel reflection coefficients (which depend on the specular reflection angle, and the electrical properties of the facets). However there is no simple extension for rough surface scattering, and the model uses a semi-empirical term that modifies (reduces) the smooth surface Fresnel reflection coefficient. It is proposed that spec is defined as the power reduction factor due to the rough surface effect alone; that is, it does not take account of reflected power variation due to the Fresnel coefficient variation. The latter depends on the reflection angle and polarization, and therefore so would the nonspecular scattered power; this would be incompatible with the Lambertian assumption. – trans: in principle the transmitted component can also be calculated from Fresnel theory for a smooth surface, single interface. However, in practice, the situation is too complicated to model (rough surface, multiple interfaces and reflections) and an experimentally determined, empirical value for trans should be used. In principle each must satisfy the condition 0 1. There is no reason to believe that equation (9) will be satisfied, and if used to derive nonspec from spec and trans, it is possible for nonspec to become negative which is unphysical. It is proposed therefore that the non-specular fraction is derived directly from the specular fraction, ignoring the transmitted component: (10) In practice trans is likely to be quite small (e.g. 10 dB building penetration loss implies trans = 0.1). Calculation of spec spec is the power reduction factor applied to the specular reflection coefficient to account for the effect of surface roughness on specular reflection. It is: (11) When calculating the specular reflection coefficient, the effective reflection coefficient R is obtained by multiplying the Fresnel coefficient RF by s: (12) s can be calculated from: (13) where: (14)
FASCOD uses a line-by-line model and takes into account all parameters characterizing the absorption lines (intensity, transition probability, etc.). It is based on the high-resolution molecular absorption database, HITRAN. The principal line parameters included in HITRAN are the resonance frequency, line intensity at 296 K, probability of a transition, half-width of the line at 296 K, and the low energy or fundamental molecular state. There are three linked models developed in the Air Force Geophysics Laboratory (AFGDL) with various spectral resolutions: – LOWTRAN 7 – Low Resolution Transmission – Spectral resolution is 20 cm−1 (equivalent to 600 GHz) in 5 cm−1 steps. – MODTRAN 3 – Moderate Resolution Transmission – Spectral resolution is 2 cm−1 (equivalent to 60 GHz) in 1 cm−1 steps. – HITRAN 2004 – High Resolution Transmission – Spectral resolution is 0.001 cm−1 (equivalent to 30 MHz). All of the models contain spectral information about many atmospheric species including H2O, O3, N2O, CO, CH4, O2, NO, NO2, SO2, and HNO3. (HITRAN includes details of over 1 000 000 absorption lines for 37 molecules.) In addition the three models include the H2O continuum across the entire spectrum, the N2 continuum in the 2 000 to 2 700 cm−1 region, molecular scattering, together with absorption and scattering from aerosol, fog, rain and clouds.
When an upper decile deviation of the noise figure for at least one noise component exceeds 12 dB, the σT calculated by equations (17) to (20), using the upper decile deviations of the noise components, should be restricted to a maximum value of: dB (23) γT is the noise factor for the simple power sum of the individual median noise factors: W (24) Similarly, when a lower decile deviation of the noise figure for at least one noise component exceeds 12 dB, the T calculated by equations (17) to (20), using the lower decile deviations of the noise components, should be restricted to the maximum value given by equation (23). Expected values of atmospheric noise, Fam (dB above kT0b at 1 MHz) (Winter; 0000-0400 LT) Expected values of atmospheric radio noise, Fam (dB above kT0b at 1 MHz) (Winter; 0400-0800 LT) Expected values of atmospheric radio noise, Fam (dB above kT0b at 1 MHz) (Winter; 0800-1200 LT) Expected values of atmospheric radio noise, Fam (dB above kT0b at 1 MHz) (Winter; 1200-1600 LT)
Expected values of atmospheric noise, Fam (dB above kT0b at 1 MHz) (Spring; 2000-2400 LT) Expected values of atmospheric radio noise, Fam (dB above kT0b at 1 MHz) (Summer; 0000-0400 LT) Expected values of atmospheric radio noise, Fam (dB above kT0b at 1 MHz) (Summer; 0400-0800 LT) Expected values of atmospheric radio noise, Fam (dB above kT0b at 1 MHz) (Summer; 0800-1200 LT) Expected values of atmospheric radio noise, Fam (dB above kT0b at 1 MHz) (Summer; 1200-1600 LT) Expected values of atmospheric radio noise, Fam (dB above kT0b at 1 MHz) (Summer; 1600-2000 LT) Expected values of atmospheric noise, Fam (dB above kT0b at 1 MHz) (Summer; 2000-2400 LT)
pr : power (W) available from an isotropic antenna located at this point  : wavelength (m). 3 The free-space basic transmission loss for a radar system (symbols: Lbr or A0r) systems represent a special case because the signal is subjected to a loss while propagating both from the transmitter to the target and from the target to the receiver. For radars using a common antenna for both transmitter and receiver, a radar free-space basic transmission loss, Lbr, can be written as follows: Lbr  103.4  20 log   40 log d – 10 log mmmmmmdB (6) where:  : radar target cross-section (m2) d : distance from the radar to the target (km) f : frequency of the system (MHz). The radar target cross-section of an object is the ratio of the total isotropically equivalent scattered power to the incident power density. 4 Conversion formulae On the basis of free-space propagation, the following conversion formulae may be used. Field strength for a given isotropically transmitted power: E  Pt – 20 log d  74.8 (7) Isotropically received power for a given field strength: Pr  E – 20 log f – 167.2 (8) Free-space basic transmission loss for a given isotropically transmitted power and field strength: Lbf  Pt – E  20 log f  167.2 (9) Power flux-density for a given field strength: S  E – 145.8 (10) where: Pt : isotropically transmitted power (dB(W)) Pr : isotropically received (dB(W)) E : electric field strength (dB(V/m)) f : frequency (GHz) d : radio path length (km) Lbf : free-space basic transmission loss (dB) S : power flux-density (dB(W/m2)). Note that equations (7) and (9) can be used to derive equation (4).
For a multipoint obstruction: (111) 2 Cylinder parameters The cylinder parameters illustrated in Fig. 8c) can now be calculated for each of the terrain obstacles defined by the string analysis: d1 and d2 are the positive inter-vertex distances to the obstacles (or terminals) on the transmitter and receiver sides of the obstacle respectively, and: (112) To calculate the cylinder radius use is made of two further profile samples: p: the point adjacent to x on the transmitter side, and: q: the point adjacent to y on the receiver side. Thus the profile indices p and q are given by: p = x – 1 (113) and: q = y + 1 (114) If a point given by p or q is a terminal, then the corresponding value of h should be the terrain height at that point, not the height above sea level of the antenna. The cylinder radius is calculated as the difference in slope between the profile section p-x and y-q, allowing for Earth curvature, divided by the distance between p and q. The distances between profile samples needed for this calculation are: dpx = dx – dp (115) dyq = dq – dy (116) dpq = dq – dp (117) The difference in between the p-x and y-q profile sections is given in radians by: (118) ae is the effective Earth radius. The cylinder radius is now given by: (119) where ν is the dimensionless knife-edge parameter in equation (32).
(122) (hr)i, the height of the ray above a straight line joining sea level at u and v at the i-th profile point is given by: (hr)i = (hu · div+hv · dui) / duv (123) (ht)i, the height of the terrain above a straight line joining sea level at u and v at the i-th profile point is given by: (ht)i =hi+dui · div / 2ae (124) The minimum value of normalized clearance is used to compute the knife-edge diffraction geometrical parameter for the most significant sub-path obstruction: (125) The sub-path diffraction loss L" is now obtained from equation (31) or Fig. 9. For some applications it may be undesirable to include sub-path diffraction enhancements. In this case a value of L" should be set to zero when it would otherwise be negative.
water, it is possible for surface reflections to contribute to ionospheric propagation, with a consequent reduction in losses. The following method does not attempt to estimate this effect. 5.1 Derivation of foEs For a given p% time, set the percentage-time values used for interpolation or extrapolation. p1 and p2, according to Table 1. 1 Conditions for setting p1 and p2 p% time p1 p2 p < 1% 0.1% 1% 1% ≤ p ≤ 10% 1% 10% 10% < p 10% 50% For a given location, obtain foEs1 and foEs2 from the maps of foEs exceeded for p1 and p2% time respectively. Calculate foEs exceeded for p% time using: (MHz) (7) 5.2 Horizon elevation angles Additional attenuation can be caused by terrain obstruction at either terminal. For each terminals, find the terrain along the great-circle path from the terminal towards the other terminal with the highest elevation angle above the local horizontal as viewed from the terminal. The elevation angle of a given terrain point is given by: (radians) (8) where: dp: distance to terrain point, km; hp : height of terrain point, m above sea level; ha : height of terminal antenna, m above sea level. Perform this calculation twice, once for each terminal, to obtain the following: εha,b: elevation angle to horizon at 1st, 2nd terminal, radians; dha,b: distance to horizon at 1st, 2nd terminal, km. 5.3 Calculation for 1-hop propagation Obtain foEs as calculated by equation (7) for the mid-point of the path to obtain the ionospheric loss for one hop, Γ1, using equation (3). Calculate the slope path length: (km) (9) Free-space loss can now be calculated for the slope distance: (dB) (10) The ray take-off angle above the local horizontal at both terminals for 1 hop is given by:
(22a) For 54 GHz < f 60 GHz: (22b) For 60 GHz < f 62 GHz: (22c) For 62 GHz < f 66 GHz: (22d) For 66 GHz < f 120 GHz: (22e) For 120 GHz < f 350 GHz: (22f) with: (22g) (22h) (22i) (22j) (22k) (22l) (22m) (22n) (22o) (22p) (22q) (22r) (22s) (22t) (22u) where: f : frequency (GHz)
(11) The attenuation coefficients, sk, are determined by the characteristic equation: where: , (n = 1, …, N-1), and (12) where N is an odd integer chosen as a compromise for computing time. Large values of N will dramatically increase computation time. Reasonable values have been determined as 11 ≤ N ≤ 21. The left hand side of (10) will be equal to 1 for values of s, which represent the roots of this equation. It will yield N + 1 roots, for which the following applies: The amplitude factors, Ak, are determined by a system of linear equations given by: for (13) n = δn = 0 for and δn = 1 for 3.2.5 Combination of the individual components The total loss, Ltotal, experienced by a signal propagating through trees is then given by the combination of loss terms: (14)
converting geometric height h to the corresponding geopotential height and calculating the temperature and pressure at the corresponding geopotential height . In the height regime, the temperature T (K) at geopotential height (km) is: T()  288.15 − 6.5 for 0  11 (2a) T()  216.65 for 11  20 (2b) T()  216.65 + (−20) for 20  32 (2c) T()  228.65 + 2.8 (−32) for 32  47 (2d) T()  270.65 for 47  51 (2e) T()  270.65 – 2.8 (−51) for 51   71 (2f) T()  214.65 – 2.0 (−71) for 71   84.852 (2g) and the pressure P (hPa) at geopotential height (km) is: P()  for 0   11 (3a) P()  for 11   20 (3b) P()  for 20   32 (3c) P()  for 32   47 (3d) P()  for 47   51 (3e) P()  for 51   71 (3f) P()  for 71   84.852 (3g) In the second height regime, the temperature T (K) at geometric height h (km) is: T(h)  186.8673 for 86  h 91 (4a) T(h)  for 91  h  100 (4b) and the pressure P (hPa) at geometric height h (km) is: P(h)  for 86  h  100 (5) where For reference, the temperature and pressure vs. geometric height are in Figs 1 and 2, respectively. FIGURE 1 Temperature vs. Geometric Height FIGURE 2 Pressure vs. Geometric Height
(dB/km) (1) where: c : specific attenuation (dB/km) within the cloud Kl : cloud liquid water specific attenuation coefficient ((dB/km)/(g/m3)) M : liquid water density in the cloud or fog (g/m3) f: frequency (GHz) T : cloud liquid water temperature (K). At frequencies of the order of 100 GHz and above, attenuation due to fog may be significant. The liquid water density in fog is typically about 0.05 g/m3 for medium fog (visibility of the order of 300 m) and 0.5 g/m3 for thick fog (visibility of the order of 50 m). 2 Cloud liquid water specific attenuation coefficient A mathematical model based on Rayleigh scattering, which uses a double-Debye model for the dielectric permittivity ( f ) of water, can be used to calculate the value of Kl for frequencies up to 200 GHz: (dB/km)/(g/m3) (2) where f is the frequency (GHz), and: (3) The complex dielectric permittivity of water is given by: (4) (5) where: 0 = 77.66 + 103.3 ( – 1) (6) 1 = 0.0671 (7) 2 = 3.52 (8) = 300 / T (9) and T is the liquid water temperature (K). The principal relaxation frequency, fp, and secondary relaxation frequency, fs, are: fp = 20.20 – 146 ( – 1) + 316 ( – 1)2 (GHz) (10) fs = 39.8fp (GHz) (11) 3 Cloud attenuation along slant paths If local measured data of the total columnar content of cloud liquid water, L (kg/m2 or, equivalently, mm), is not available, the method in § 3.1 should be used to predict the cloud attenuation along slant paths. This prediction method is based on ERA-40 data where the total columnar content of cloud liquid water reduced to a fixed temperature of 273.15 K, Lred (kg/m2 or, equivalently, mm), is used. If local measured data of the total columnar content of cloud liquid water, L, is available from other sources, e.g. from ground radiometric measurements, Earth observation products or meteorological
TABLE 1  and Q1 values for various propagation effects and locations Rain effect terrestrial attenuation Rain effect slant path attenuation Rain rate Multipath land sea Global 0.13, 2.85 0.13, 2.85 0.13, 2.85 0.13, (Ns/75) 0.13, (Ns/75) Tropical, subtropical and temperate climate regions with frequent rain 0.15, 2.82 Dry temperate, polar and desert regions 0.11, 4.48 Europe West 0.13, 3.0 0.16, 3.1 0.13, 4.0 0.18, 3.3 Europe North West 1.3 GHz 0.11, 4.9 Europe North West 11 GHz 0.19, 3.7 Europe Mediterranean 0.14, 2.6 0.16, 3.1 Europe Nordic 0.15, 3.0 0.16, 3.8 0.12, 5.0 Europe alpine 0.15, 3.0 0.16, 3.8 Europe Poland 0.18, 2.6 Europe Russian Federation 0.14, 3.6 Europe UK 40 and 50 GHz 0.13, 2.54 Congo 0.25, 1.5 Canada Prairie and North 0.08, 4.3
Australia Subtropical/ coastal 0.15, 3.15 TABLE 1 (end) Rain effect terrestrial attenuation Rain effect slant path attenuation Rain rate Multipath land sea Australia Tropical/arid 0.12, 4.35 Brazil Equatorial 0.13, 2.85 Brazil Tropical maritime 0.21, 2.25 Brazil Tropical inland 0.13, 3.00 Brazil Subtropical 0.13, 2.85 Indonesia 0.22, 1.7 Japan Tokyo 0.20, 3.0 Japan Yamaguchi 0.15, 4.0 Japan Kashima 0.15, 2.7 Korea 0.12, 4.6 Kyrgyzstan Flat regions 0.09, 5.95 Kyrgyzstan Mountainous regions 0.10, 6.70 Kyrgyzstan Coastal region of Ysyk-Kol lake 0.14, 4.73 China South 0.15, 3.12 China North 0.13, 4.12 China Desert 0.10, 5.40
3.1 Simulation network model 11 3.2 Bandwidth On Demand (BOD) scheme used in OPNET simulations 12 3.2.1 Return channel bandwidth allocation algorithm 12 3.3 Simulation experiments and performance results – Scenario 1 14 3.3.1 Simulation model 14 3.3.2 Simulation experiment results 15 3.3.3 Summary 21 3.4 Simulation experiments and performance results – Scenario 2 21 3.4.1 Simulation network model 21 3.4.2 QoS provisioning 22 3.4.3 Traffic model 22
RECOMMENDATION ITU-R SA.1018-1 Hypothetical reference system for networks/systems comprising data satellites in the geostationary orbit and their user spacecraft in lowEarth orbits (Question ITU-R 117/7) (1994-2017) Scope This Recommendation provides architecture and characterization of a hypothetical reference system for network/systems comprising data relay satellites. Keywords DRS, Earth-to-space, space-to-space, forward feeder link, return feeder link Related ITU-R Recommendations and Reports Recommendations ITU-R SA.510, ITU-R SA.1019, ITU-R SA.1155, ITU-R SA.1274, ITU-R SA.1275, ITU-R SA.1276, ITU-R SA.1414. The ITU Radiocommunication Assembly, considering a) that communications between the ground and low-orbiting spacecraft and launch vehicles used for space research, Earth exploration and other purposes is essential; b) that such communications may be required to be continuous or near continuous; c) that such communications may be required while the spacecraft are passing over specific points on the Earthʼs surface; d) that a land-based station has only limited visibility of a low-orbiting spacecraft; e) that available land-based stations are only able to cover limited portions of any low orbit; f) that it is not economically or practically feasible to extend networks of stations to provide full or more complete coverage; g) that a data relay satellite (DRS) in geostationary orbit can provide communications between a single earth station and a low-orbiting spacecraft for more than one-half of its orbit (see description in Annex); h) that two such DRSs, suitably located in geostationary orbit, with a wide separation angle, can provide communications between two co-located earth stations and a low-orbiting spacecraft almost continuously, with the exception only of a zone of exclusion (ZOE), above the part of the Earth opposite to these earth stations; i) that two such DRSs, suitably placed in geostationary orbit, can provide fully-continuous coverage between two separate earth stations and a low-orbiting spacecraft; j) that a DRS system comprising two DRSs can serve several user spacecraft simultaneously, and many more user spacecraft by means of time-sharing; k) that a DRS system can also serve additional earth stations, either both transmitting and receiving or only receiving signals from user spacecraft;
Reliability/integrity: The DBMS engine should guarantee that every transaction that was executed successfully will not be lost despite a system failure. Transaction operations: Transaction based databases guarantee that an operation will be done in a discrete fashion. The operation will be done completely or not at all. This capability guarantees semantic integrity in the database. Database definition languages also include the ability to impose constraints in order to assure referential integrity in the data. Multiuser: The DBMS engine should multiple users to be connected to the database and handle concurrent access to the information. A large number of users can be connected to the system. Contentions: The database will handle the contentions of users trying to access the same piece of data and appropriately lock data that are being updated. The database should implement the data content recommended by the ITU publications. The following types of data may be stored in the database: – National Table of Frequency Allocations – Frequency assignments – Block assignments for concessions – Licence/concession holder – Equipment characteristics – Monitoring – Applications – Fees – Complaints – Violations/infractions – Spectrum occupancy statistics – Unidentified transmitters – Assigned frequency(ies) – Cancelled licences. Appropriate descriptions of the transmitter, receiver and antenna characteristics are essential for optimal spectrum management. In order to facilitate data entry, the system should highlight the suitable fields and suggest defaults according to the designation of emission or type of service. For example, only for broadcasting TV (BT) should the system prompt for TV. When the antenna pattern is unknown, the system should estimate the side-lobes using an appropriate reference radiation pattern, such as given in Recommendation ITU-R F.699. All data needed to define the site should be included: coordinates, height above sea level from the digital terrain map. The specific azimuth and elevation angles are part of the station defined in the licence. The data elements in the system should be based on the latest edition of the ITU Handbook on computer-aided techniques for spectrum management. To ease data input, the operator should be allowed to choose the element from predetermined tables; the system should be capable of using defaults for most inputs. Screens should allow “remarks” to add information not coded as data elements to be recorded. Where applicable, the definitions of the fields should be in accordance with the Preface to the BR IFIC and the RDD (Recommendation ITU-R SM.1413).
TABLE 5 Table of break points corresponding to Fig. 17 for 6 MHz DVB-T systems Frequency relative to the centre of the 6 MHz channel (MHz) Relative level in a 4 kHz measurement bandwidth (dB) 15 99 9 91 3.2 66.5 2.86 31.5 2.86 31.5 3.2 66.5 9 91 15 99 TABLE 6 Table of end point value and next-to-end point values to be used in conjunction with Fig. 17 and Table 5, applicable to a range of transmitter output powers, for 6 MHz DVB-T systems End point value(1) (4 kHz measurement bandwidth) (dB) Power range (dBW) Corresponding spurious level (100 kHz measurement bandwidth) 89 – (P – 9) P 9 36 dBm 89 9 < P 29 75 dBc 89 – (P – 29) 29 < P 39 16 dBm 99 39 < P 50 85 dBc 99 – (P – 50) 50 P 5 dBm (1) The next-to-end point value is 8 dB higher than the end point value and all of these values are subject to an upper limit equal to –66.5 dB. 1.2 6 MHz channelling ISDB-T systems For 6 MHz ISDBT systems, the OoB domain extends from 3 MHz (i.e. 0.5 6 MHz) to 15 MHz (i.e. 2.5 6 MHz) relative to channel centre. Spectrum limit mask for a 6 MHz ISDBT system is shown in Fig. 18. The related break points are given in Table 7. The relative power level is defined in a reference bandwidth of 4 kHz. The 0 dB reference level corresponds to the mean output power measured in the channel bandwidth. These emission limits apply when transmitter power is above 39 dBW. FIGURE 18 Spectrum mask for 6 MHz ISDB-T (for P > 39 dBW)
0.77 –26 0.97 –52 22 End point values to be used in conjunction with Table 21 Digital System A operating in the 47-68 MHz and 174-240 MHz End value(1) (dB/4 kHz) Power range (dBW) Corresponding spurious level (100 kHz measurement bandwidth) 89 – (P – 9) P 9 36 dBm –89 9  P 29 75 dBc 89 – (P – 29) 29  P 39 16 dBm –99 39  P 50 85 dBc 99 – (P – 50) 50  P 5 dBm Digital System A operating in the band 1 452-1 467.5 MHz End point value(1) (dB/4 kHz) Power range (dBW) Corresponding spurious level (1 MHz measurement bandwidth) 99 – (P – 9) P 9 36 dBm –99 9  P 29 75 dBc 99 – (P – 29) 29  P 39 16 dBm 106 39  P 50 85 dBc 106 50  P 5 dBm (1) The end point value is subject to an upper limit equal to –52 dB and a lower limit equal to –106 dB. Annex 8 OoB domain emission limits for primary radar systems 1 Introduction The RR define “primary radar” as “A radiodetermination system based on the comparison of reference signals with radio signals reflected from the position to be determined”. Terrestrial primary radars operate in the radionavigation service (air surveillance radars and navigation radars on aircraft and ships), the meteorological aids service (weather radars), and the radiolocation service (most other terrestrial radars). Space-based radars include active remote sensing satellites operating in the SRS (active) and EESS (active), and other radars in the SRS.
a length in the range of the TDMA bursts. Therefore, it is necessary to select a measurement frequency where short bursts of radiation, such as TDMA, do not appear. This can be implemented by checking the type of radio service allocated to the measurement frequency at the measurement location. References Recommendation ITUR P.372 − noise. Report ITUR SM.2055 − Radio noise measurements. Report ITUR SM.2155 − Man-made noise measurements in the HF range. Report ITUR SM.2157 − Measurement methods for power line high data rate telecommunication systems.
VHF 70 0.2 .5 3 6.3 3.3 9 12.3 95 1.64 10.3 19.3 99 2.33 14.7 23.7 UHF 70 0.2 .5 6 8.1 4.2 11 15.2 95 1.64 13.3 24.3 99 2.33 18.9 29.9 NOTE – The values are based on Recommendation ITU-R P.1812-2. If, as recommended, the measurement is done mobile, the standard deviation σ1 for broadband signals does not for the following reasons: – the measurement was actually taken where reception is to be assessed; – the measurement method provides so many samples that the calculated median of all measurement samples already represents the actual median field strength inside the measurement area. The total correction to be applied to these measurement values are summarized in Table 10. TABLE 10 Total correction for DVBT indoor coverage when measured mobile Frequency (MHz) Wanted location probability (%) µ σ (dB) Cl (dB) Building attenuation (dB) Total correction (dB) VHF 70 0.2 3 1.6 9 10.6 95 1.64 4.9 13.9 99 2.33 7.0 16.0 UHF 70 0.2 .5 2.9 8 10.9 95 1.64 9.0 17.0 99 2.33 12.8 20.8 ______________
systems (e.g. GSO satellites or multiple-satellite systems) a systematic adjustment of the levels in Recommendation ITUR RA.769 may be warranted. Accordingly, when the levels contained in Table 8 are applied or referred to, account should be taken of the assumptions used to derive them. TABLE 8 Threshold levels of pfd of interference detrimental to the radio astronomy service* Continuum observations Spectral lines observations Radio astronomy band(1) (MHz) pfd (dB(W/m2)) Assumed bandwidth (MHz) pfd (dB(W/m2)) Assumed spectral line channel bandwidth (kHz) 13.36-13.41 –201 0.05 (2) (2) 25.55-25.67 –199 0.120 (2) (2) 73.0-74.6 –196 1.6 (2) (2) 150.05-153.0 –194 2.95 (2) (2) 322.0-328.6 –189 6.6 –204 10 406.1-410.0 –189 3.9 (2) (2) 608-614 –185 6 (2) (2) 1 400-1 427 –180 27 –196 20 1 610.6-1 613.8 (3) (3) –194 20 1 660-1 670 –181 10 –194 20 2 690-2 700 –177 10 (2) (2) 4 990-5 000 –171 10 (2) (2) (GHz) 10.6-10.7 –160 100 (2) (2) 15.35-15.4 –156 50 (2) (2) 22.21-22.5 (3) (3) –162 250 23.6-24.0 –147 400 –161 250 31.3-31.8 –141 500 (2) (2) 42.5-43.5 –137 1 000 –153 500 86-92 –125 6 000 –144 1 000 105-116 –121 11 000 –141 1 000 164-168 –120 4 000 (2) (2) 182-185 (3) (3) –136 1 500 217-231 –114 14 000 –133 2 500 265-275 –113 10 000 –131 2 500
105-126 –160 200 150-151 –160 200 155.5-158.5 –160 200 164-168 –160 200 175-192 –160 200 9 (end ) Frequency (GHz) Interference level (dBW) Interference reference bandwidth (MHz) 200-202 –160 200 217-231 –160 200 235-238 –160 200 250-252 –160 200 275-277 –160 200 300-302 –160 200 324-326 –160 200 345-347 –160 200 363-365 –160 200 379-381 –160 200 (1) This value is under study. (2) Second number for pushbroom sensors. Annex 4 List of ITU-R Recommendations relating to spurious emissions for some specific services Recommendation ITU-R SM.239 Spurious emissions from sound and television broadcast receivers Recommendation ITU-R S.726 Maximum permissible level of spurious emissions from very small aperture terminals (VSATs) Recommendation ITU-R RA.611 Protection of the radioastronomy service from spurious emissions Recommendation ITU-R M.1177 Techniques for measurement of unwanted emissions of radar systems Recommendation ITU-R F.1191 Bandwidths and unwanted emissions of digital fixed service systems
Amateur services operating below 30 MHz (including with SSB)(9) –13 dBm if PEP  5 W 10 log PEP – 20 if PEP  5 W Services operating below 30 MHz, except space, radiodetermination, broadcast, those using SSB from mobile stations, and amateur(9) –13 dBm if X  50 W 10 log X – 30 if X  50 W X  PEP for SSB modulation X  P for modulation TABLE 10 (end) Service category in accordance with RR Article 1 or equipment type(1), (2) Maximum permitted spurious domain emission power in the relevant reference bandwidth (see recommends 4.1) (dBm) with P, PEP or X (W) Low power device radio equipment(10) –26 dBm if P  0.025 W 10 log P – 10 if 0.025 W  P  0.100 W EPIRB, ELT, PLB, SART, ship emergency, lifeboat, and survival craft transmitters, land, aeronautical or maritime transmitters when used in emergency No limit
2.3.3 Spurious responses Spurious responses to unwanted signals can be expected to occur in receivers at frequencies related to the receiver local oscillator frequency (lo)and the receiver intermediate frequencies (IF). The frequencies at which spurious responses can occur should be calculated using the following expressions. q fsp  nflo  fIF where: q: harmonic order of the mixer input signal fsp : frequency at which a spurious response may occur n: harmonic order of the local oscillator flo : frequency of the local oscillator applied to the mixer stage The above equation provides the receiver spurious response frequency which produces a signal at the centre of the receiver IF band. Therefore, receiver spurious responses may occur over a frequency range of plus or minus one-half the receiver IF bandwidth. The protection which applies when the vision or sound carrier of a TV signal occurs at these spurious response frequencies is typically 70 dB. Under these circumstances, the power of the relevant carrier (vision or sound) should be used when calculating the level of the unwanted signal. 3. Protection margin 3.1 Assessment of the protection margin The protection margin (PM) is given by: PM (dB) = FS – NF – AF where: FS: minimum field-strength value (dB(V/m)) given in § 1 NF: nuisance field and is determined by: NF = FI + PR FI: interfering field strength of the broadcasting signal. The appropriate propagation curves for 10% of time and 50% of locations of Recommendation ITU-R P.1546 should be used PR: protection (dB) given in § 2 of this Annex AF: adjustment factor (dB) to deal with receiver antenna gain discrimination and polarization discrimination (see § 4). The calculated protection margin should be positive at all locations the fixed service is required. 4. Additional factors to consider 4.1 Receiving antenna discrimination The receiving antenna discrimination is determined by taking into account the receiver antenna gain in the direction of the TV broadcasting station. See Recommendation ITU-R F.699 for determination of the receiving antenna discrimination. 4.2 Receiving antenna cross-polarization discrimination For fixed stations, the value of the antenna discrimination against orthogonal polarization could be up to 15 dB in the mainbeam. Where non-orthogonal or mixed polarization are used, no antenna polarization discrimination should be taken into account.
6B/145 Proposed working document towards a draft new Recommendation on digital interfaces for UHDTV studio signals Japan 6B/155 Proposed new Recommendation ITU-R BT [UHDTVTAILOR] – Tailoring of UHDTV programmes for their distribution and broadcasting in HDTV BBC, CBS, Inc. 6B/156 Proposed preliminary draft new Recommendation ITUR BT.[UHDTV-IF] – Transport of ultra-high definition digital television programmes for international programme exchange in broadcasting Australia 6C/257 5 Preliminary revision of Recommendation ITUR BT.2020 – Parameter values for ultra-high definition television systems for production and international programme exchange Chairman, WP 6C 6C/257 Annex 9 Working document towards a draft revision of Report ITU-R BT.2246 – The present state of ultra-high definition television Chairman, WP 6C 6C/257 Annex11 Appointment of a Rapporteur to complete a draft revision of Report ITU-R BT.2246 – The present state of definition television Chairman, WP 6C 6B/180 Annex 2 Working document towards a new Recommendation ITU-R BT.[UHDTV-TAILOR] – Tailoring of UHDTV programmes for their distribution and broadcasting in HDTV Chairman, WP 6B 6B/180 Annex 3 Working document towards a draft new Recommendation ITUR BT.[UHDTV-IF] – Real-time digital interfaces for UHDTV studio signals Chairman, WP 6B Annex 2 Analysis of sub-sampled versions of the UHDTV signals 1 Summary See § 3.2.7.2. 2 Fundamental 2.1 Why YC transmission is needed The YC format, in which image data is handled as one luminance signal and two colour signals, was first used in the early days of colour television. Its primary advantages include compatibility with conventional (i.e. black and white) television and its ability to reduce bandwidth when applied to a high