PATENT DOCUMENT

Publication Number: US-9838025-B1
Application Number: US-201615233124-A
Country: US
Kind Code: B1

Title: Method for reducing lock time in a closed loop clock signal generator

Abstract:
An apparatus includes circuitry and an oscillator circuit that may be configured to generate a clock signal dependent upon a control signal. The circuitry may be configured to perform a frequency measurement of the clock signal. In response to a determination that the frequency of the clock signal is greater than a first threshold, the circuitry may also be configured to perform a phase comparison between a divided clock signal and a reference clock signal, and to adjust a value of the control signal such that the adjusted value depends upon a result of the comparison. In response to a determination that the frequency of the clock signal is less than the first threshold, the circuitry may be configured to adjust the value of the control signal such that the adjusted value depends upon a result of the measurement.

Claims:
What is claimed is: 
     
       1. An apparatus, comprising:
 an oscillator circuit configured to generate a clock signal dependent upon a control signal; 
 a charge pump configured to use a current source to generate an output current; and 
 circuitry configured to:
 perform a measurement of a frequency of the clock signal; 
 perform a comparison of a phase of a divided clock signal to a phase of a reference clock signal in response to a determination that the frequency of the clock signal is greater than a first threshold frequency, wherein the phase of the divided clock signal is dependent upon a phase of the clock signal; 
 in response to the determination that the frequency of the clock signal is greater than the first threshold frequency, adjust a value of the control signal such that the adjusted value depends upon a result of the comparison; and 
 in response to a determination that the frequency of the clock signal is less than the first threshold frequency, adjust the value of the control signal by adjusting the current source based on a result of the measurement. 
 
 
     
     
       2. The apparatus of  claim 1 , wherein the circuitry includes a phase detection circuit configured to perform the comparison, and wherein the circuitry is further configured to decouple the divided clock signal from an input node of the phase detection circuit in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     
     
       3. The apparatus of  claim 2 , wherein the circuitry is further configured to decouple an output of the phase detection circuit from an input node of the charge pump in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     
     
       4. The apparatus of  claim 1 , wherein the circuitry includes a frequency divider circuit configured to generate the divided clock signal based on the clock signal, and wherein the circuitry is further configured to place the frequency divider circuit into a reduced power mode in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     
     
       5. The apparatus of  claim 1 , wherein the circuitry includes a low pass filter circuit, and wherein the circuitry is further configured to adjust a frequency response of the low pass filter circuit in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     
     
       6. The apparatus of  claim 1 , wherein the circuitry includes a phase detection circuit and wherein the circuitry is further configured to place the phase detection circuit into a reduced power mode in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     
     
       7. The apparatus of  claim 1 , wherein the circuitry is further configured to:
 in response to a determination that the frequency of the clock signal is less than a second threshold frequency, adjust the value of the control signal such that the adjusted value depends upon the result of the comparison, wherein the second threshold frequency is greater than the first threshold frequency; and 
 in response to a determination that the frequency of the clock signal is greater than the second threshold frequency, adjust the value of the control signal by adjusting the current source based on the result of the measurement. 
 
     
     
       8. A method for operating a clock generation circuit, comprising:
 generating a clock signal dependent upon a control signal; 
 performing a measurement of a frequency of the clock signal; 
 performing a comparison of a phase of a divided clock signal to a phase of a reference clock signal in response to determining that the frequency of the clock signal is greater than a first threshold frequency, wherein the phase of the divided clock signal is dependent upon a phase of the clock signal; 
 charging, using at least one current source, a capacitor such that an amount of charge stored in the capacitor depends upon the result of the comparison; 
 adjusting a value of the control signal such that the adjusted value depends upon a result of the comparison in response to determining that the frequency of the clock signal is greater than the first threshold frequency; and 
 adjusting the value of the control signal by adjusting the at least one current source based on a result of the measurement in response to determining that the frequency of the clock signal is less than the first threshold frequency. 
 
     
     
       9. The method of  claim 8 , further comprising suspending performance of the comparison by decoupling the divided clock signal from a phase detection circuit in response to determining that the frequency of the clock signal is less than the first threshold frequency. 
     
     
       10. The method of  claim 8 , wherein adjusting the value of the control signal by adjusting the at least one current source includes enabling the at least one current source to increase the amount of charge stored in the capacitor. 
     
     
       11. The method of  claim 8 , further comprising:
 filtering the control signal using a low pass filter; and 
 adjusting a frequency response of the low pass filter in response to determining that the frequency of the clock signal is less than the first threshold frequency. 
 
     
     
       12. The method of  claim 8 , further comprising disabling a portion of the clock generation circuit in response to determining that the frequency of the clock signal is less than the first threshold frequency. 
     
     
       13. The method of  claim 8 , further comprising:
 in response to determining that the frequency of the clock signal is less than a second threshold frequency, adjusting the value of the control signal such that the adjusted value depends upon the result of the comparison, wherein the second threshold frequency is greater than the first threshold frequency; and 
 in response to determining that the frequency of the clock signal is greater than the second threshold frequency, adjusting the value of the control signal by adjusting the at least one current source based on the result of the measurement. 
 
     
     
       14. The method of  claim 13 , wherein adjusting the value of the control signal by adjusting the at least one current source includes disabling the at least one current source and enabling a current sink to decrease the amount of charge stored in the capacitor. 
     
     
       15. A system, comprising:
 an oscillator circuit configured to generate a reference clock signal; 
 a processor configured to set a value in a register; and 
 a clock generation circuit configured to:
 generate a clock signal dependent upon the reference clock signal and the value in the register; 
 perform a measurement of a frequency of the clock signal; 
 perform a comparison of a phase of a divided clock signal to a phase of the reference clock signal in response to a determination that the frequency of the clock signal is greater than a first threshold frequency, wherein the phase of the divided clock signal is dependent upon a phase of the clock signal; 
 in response to the determination that the frequency of the clock signal is greater than the first threshold frequency, adjust a value of a control signal such that the adjusted value depends upon a result of the comparison, wherein the frequency of the clock signal is dependent upon the value of the control signal; and 
 in response to a determination that the frequency of the clock signal is less than the first threshold frequency, adjust the value of the control signal such that the adjusted value depends upon a result of the measurement. 
 
 
     
     
       16. The system of  claim 15 , wherein the clock generation circuit includes a phase detection circuit configured to perform the comparison, and wherein the clock generation circuit is further configured to decouple the clock signal from an input node of the phase detection circuit in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     
     
       17. The system of  claim 16 , wherein the clock generation circuit includes a charge pump configured to generate an output current dependent upon a signal at an input node of the charge pump, and wherein the clock generation circuit is further configured to decouple an output of the phase detection circuit from the input node of the charge pump in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     
     
       18. The system of  claim 15 , wherein the clock generation circuit includes a charge pump configured to generate an output current dependent upon a current source, and wherein the clock generation circuit is further configured to enable the current source in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     
     
       19. The system of  claim 15 , wherein the clock generation circuit includes a low pass filter circuit, and wherein the clock generation circuit is further configured to adjust a frequency response of the low pass filter circuit in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     
     
       20. The system of  claim 15 , wherein the clock generation circuit is further configured to:
 in response to a determination that the frequency of the clock signal is less than a second threshold frequency, adjust the value of the control signal such that the adjusted value depends upon the result of the comparison, wherein the second threshold frequency is greater than the first threshold frequency; and 
 in response to a determination that the frequency of the clock signal is greater than the second threshold frequency, adjust the value of the control signal such that the adjusted value depends upon the result of the measurement.

Description:
BACKGROUND 
     Technical Field 
     Embodiments described herein are related to the field of integrated circuit implementation, and more particularly to the implementation of clock signal generators. 
     Description of the Related Art 
     Systems-on-a-chip (SoCs) designs may include one or more closed-loop clock signal generators, configured to output a clock signal at a target frequency. Closed-loop clock signal generators may utilize a reference clock to generate output clock signals of a different frequency than the reference clock. In some embodiments, the target frequency may be programmable, allowing a processor in the SoC to adjust the clock frequency to a suitable value for current operating conditions, e.g., set a low frequency value to conserve power when fewer tasks are active, or vice versa. Some examples of such closed-loop clock generators include phase-locked loops (PLLs), delay-locked loops (DLLs), and frequency-locked loops (FLLs). 
     Some closed-loop clock generators, such as, for example, PLLs, may experience cycle-slip when adjusting from an initial frequency to the target frequency. “Cycle-slip” may occur when a phase difference between an edge of the output clock signal and an edge of a reference clock is greater than 2π radians. Cycle-slip may cause delays for the PLL to acquire lock, i.e., generate an output clock signal at or near the target frequency. 
     SUMMARY OF THE EMBODIMENTS 
     Various embodiments of a clock generation unit are disclosed. Broadly speaking, a system, an apparatus, and a method are contemplated in which the apparatus includes circuitry and an oscillator circuit that may be configured to generate a clock signal dependent upon a control signal. The circuitry may be configured to perform a measurement of a frequency of the clock signal. The circuitry may be further configured to perform a comparison of a phase of a divided clock signal to a phase of a reference clock signal in response to a determination that the frequency of the clock signal is greater than a first threshold frequency. The phase of the divided clock signal may be dependent upon a phase of the clock signal. In response to the determination that the frequency of the clock signal is greater than the first threshold frequency, the circuitry may be configured to adjust a value of the control signal such that the adjusted value depends upon a result of the comparison. In response to a determination that the frequency of the clock signal is less than the first threshold frequency, the circuitry may be configured to adjust the value of the control signal such that the adjusted value depends upon a result of the measurement. 
     In a further embodiment, the circuitry may include a phase detection circuit configured to co perform the comparison. The circuitry may be further configured to decouple the clock signal from an input node of the phase detection circuit in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     In another embodiment, the circuitry may include a charge pump configured to generate an output current dependent upon a signal at an input node of the charge pump. The circuitry may be further configured to decouple an output of the phase detection circuit from the input node of the charge pump in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     In one embodiment, the circuitry may include a charge pump configured to generate an output current dependent upon a current source. The circuitry may be further configured to enable the current source in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     In a further embodiment, the circuitry may include a low pass filter circuit. The circuitry may be further configured to adjust a frequency response of the low pass filter circuit in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     In one embodiment, the circuitry includes a phase detection circuit. The circuitry may be further configured to place the phase detection circuit into a reduced power mode in response to the determination that the frequency of the clock signal is less than the first threshold frequency. 
     In another embodiment, in response to a determination that the frequency of the clock signal is less than a second threshold frequency, the circuitry may be further configured to adjust the value of the control signal such that the adjusted value depends upon the result of the comparison. The second threshold frequency may be greater than the first threshold frequency. In response to a determination that the frequency of the clock signal is greater than the second threshold frequency, the circuitry may be configured to adjust the value of the control signal such that the adjusted value depends upon the result of the measurement. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       The following detailed description makes reference to the accompanying drawings, which are now briefly described. 
         FIG. 1  illustrates an embodiment of a various circuit blocks coupled to a clock generation circuit. 
         FIG. 2  illustrates a block diagram of a first embodiment of a clock generation circuit. 
         FIG. 3  shows a first timing diagram illustrating possible waveforms of an embodiment of a clock generation circuit. 
         FIG. 4  illustrates a first chart showing an example of output frequency versus time of an embodiment of a clock generation circuit. 
         FIG. 5  illustrates a block diagram of a second embodiment of a clock generation circuit. 
         FIG. 6  depicts a second timing diagram illustrating possible waveforms of an embodiment of a clock generation circuit. 
         FIG. 7  shows a second chart illustrating an example of output frequency versus time of an embodiment of a clock generation circuit. 
         FIG. 8  depicts an example circuit for an embodiment of a charge pump and a low pass filter. 
         FIG. 9  shows a block diagram of a third embodiment of a clock generation circuit. 
         FIG. 10  illustrates another example circuit for an embodiment of a low pass filter. 
         FIG. 11  depicts a block diagram of a fourth embodiment of a clock generation circuit. 
         FIG. 12  illustrates a third timing diagram illustrating possible waveforms of an embodiment of a clock generation circuit. 
         FIG. 13  shows a third chart illustrating an example of output frequency versus time of an embodiment of a clock generation circuit. 
         FIG. 14  illustrates a flow diagram of an embodiment of a method for operating a closed-loop clock generation circuit. 
     
    
    
     While the disclosure is susceptible to various modifications and alternative forms, specific embodiments thereof are shown by way of example in the drawings and will herein be described in detail. It should be understood, however, that the drawings and detailed description thereto are not intended to limit the disclosure to the particular form illustrated, but on the contrary, the intention is to cover all modifications, equivalents and alternatives falling within the spirit and scope of the present disclosure as defined by the appended claims. The headings used herein are for organizational purposes only and are not meant to be used to limit the scope of the description. As used throughout this application, the word “may” is used in a permissive sense (i.e., meaning having the potential to), rather than the mandatory sense (i.e., meaning must). Similarly, the words “include,” “including,” and “includes” mean including, but not limited to. 
     Various units, circuits, or other components may be described as “configured to” perform a task or tasks. In such contexts, “configured to” is a broad recitation of structure generally meaning “having circuitry that” performs the task or tasks during operation. As such, the unit/circuit/component can be configured to perform the task even when the unit/circuit/component is not currently on. In general, the circuitry that forms the structure corresponding to “configured to” may include hardware circuits. Similarly, various units/circuits/components may be described as performing a task or tasks, for convenience in the description. Such descriptions should be interpreted as including the phrase “configured to.” Reciting a unit/circuit/component that is configured to perform one or more tasks is expressly intended not to invoke 35 U.S.C. §112, paragraph (f) interpretation for that unit/circuit/component. More generally, the recitation of any element is expressly intended not to invoke 35 U.S.C. §112, paragraph (f) interpretation for that element unless the language “means for” or “step for” is specifically recited. 
     DETAILED DESCRIPTION OF EMBODIMENTS 
     Integrated circuits (ICs), such as, e.g., a system-on-a-chip (SoC) may include multiple functional circuits utilizing one or more high frequency clock signals. In some cases, certain tasks may require the accuracy of such high frequency clock signals fall within predetermined ranges. Clock generation circuits, however, may be susceptible to changes in operating conditions, such as a voltage level of a power supply, or operating temperature, that reduce the accuracy of their generated clock signals. Additionally, in some embodiments, clock generation circuits are programmable, allowing the frequency of the generated clock signal to be adjusted during operation. 
     In some embodiments, a closed-loop clock generator may be used to generate high frequency clock signals that meet both accuracy and adjustability requirements of a given IC. A “closed-loop” clock generator, as used and described herein, refers to a clock generation circuit in which at least one parameter or condition of an output clock signal is fed back into the clock generation circuit and used to adjust the output clock signal to achieve and maintain target operating parameters of the clock signal, such as, for example, the frequency of the output clock signal. Generally speaking, a closed-loop clock generator in an IC may generate a clock signal and “lock” the clock signal at or near a target frequency. As used herein, to “lock” or “achieve lock” refers to a closed-loop clock generator generating a clock signal within a predetermined range of a target (i.e., desired or selected) frequency. In some embodiments, the target frequency may be changed during operation of the IC for any suitable reason. For example, the target frequency may be reduced to conserve power or may be increased to speed execution of a task. When a target frequency of a closed-loop clock generator is changed, the locked condition may be lost and the clock generator may operate in an unlocked state until the output frequency reaches a frequency close enough to the target frequency to satisfy the lock condition for the clock generator. 
     While a closed-loop clock generator is running in an unlocked state, a condition referred to as cycle slip may occur. Referring to a phase-locked loop (PLL) for example, the PLL compares rising or falling transitions of a reference clock signal to corresponding transitions of a feedback clock signal that is generated from an output clock signal. Depending if a feedback clock transition occurs ahead of or behind a corresponding transition of the reference clock signal, the PLL decreases or increases, respectively, the frequency of the output clock signal to bring transitions of the two clock signals closer together. When the reference clock signal and the feedback clock signal are running at different frequencies, the frequency difference accumulates as phase error. “Cycle-slip” occurs when the frequency difference persists for a sufficient time to cause the resulting phase error to be greater than the period of either clock. When cycle-slip occurs, two successive reference clock signal transitions may occur without a corresponding transition of the output clock signal. 
     The various embodiments illustrated in the drawings and described below may allow a clock signal generator to mitigate cycle slip and reduce an amount of time a closed-loop clock generator takes to achieve lock. These embodiments may employ techniques that also reduce power consumption while in the unlocked state. 
     A block diagram of an embodiment of an integrated circuit (IC) is illustrated in  FIG. 1 . In the illustrated embodiment, IC  100  includes Processing Core  101  coupled to Memory Block  102 , I/O Block  103 , Analog/Mixed-Signal Block  104 , Clock Generation Circuit  105 , all coupled through bus  110 . Additionally, Clock Generation Circuit  105  provides a clock signal  112  to the circuit blocks in IC  100 . In various embodiments, IC  100  may correspond to a system on a chip (SoC) for use in a mobile computing application such as, e.g., a tablet computer, smartphone or wearable device. 
     Processing Core  101  may, in various embodiments, be representative of a general-purpose processor that performs computational operations. For example, Processing Core  101  may be a central processing unit (CPU) such as a microprocessor, a microcontroller, an application-specific integrated circuit (ASIC), or a field-programmable gate array (FPGA). In some embodiments, Processing Core  101  may include multiple CPU cores and may include one or more register files and memories. In various embodiments, Processing Core  101  may implement any suitable instruction set architecture (ISA), such as, e.g., PowerPC™, or x86 ISAs, or combination thereof. Processing Core  101  may include one or more bus transceiver units that allow Processing Core  101  to communication to other functional circuits via bus  110 , such as, Memory Block  102 , for example. 
     Memory Block  102  may include any suitable type of memory such as, for example, a Dynamic Random Access Memory (DRAM), a Static Random Access Memory (SRAM), a Read-only Memory (ROM), Electrically Erasable Programmable Read-only Memory (EEPROM), a FLASH memory, a Ferroelectric Random Access Memory (FeRAM), Resistive Random Access Memory (RRAM or ReRAM), or a Magnetoresistive Random Access Memory (MRAM), for example. Some embodiments may include a single memory, such as Memory Block  102  and other embodiments may include more than two memory blocks (not shown). In some embodiments, Memory Block  102  may be configured to store program instructions that may be executed by Processing Core  101 . Memory Block  102  may be configured to store data to be processed, such as graphics data, for example. Memory Block  102 , may, in some embodiments, include a memory controller for interfacing to memory external to IC  100 , such as, for example, one or more DRAM chips. 
     I/O Block  103  is, in one embodiment, configured to coordinate data transfer between IC  100  and one or more peripheral devices. Such peripheral devices may include, without limitation, storage devices (e.g., magnetic or optical media-based storage devices including hard drives, tape drives, CD drives, DVD drives, etc.), audio processing subsystems, graphics processing subsystems, or any other suitable type of peripheral devices. I/O Block  103  may include general-purpose input/output pins (I/O pins). In some embodiments, I/O Block  103  may be configured to implement a version of Universal Serial Bus (USB) protocol, IEEE 1394 (Firewire®) protocol, or an Ethernet (IEEE 802.3) networking standard. 
     In the illustrated embodiment, Analog/Mixed-Signal Block  104  includes one or more analog circuits. For example Analog/Mixed-Signal Block  104  may include a crystal oscillator, an internal oscillator, a phase-locked loop (PLL), delay-locked loop (DLL), or frequency-locked loop (FLL). One or more analog-to-digital converters (ADCs) or digital-to-analog converters (DACs) may also be included in analog/mixed signal block  104 . In some embodiments, Analog/Mixed-Signal Block  104  may include radio frequency (RF) circuits that may be configured for operation with cellular telephone networks, or other suitable RF-based networks. Analog/Mixed-Signal Block  104  may include one or more voltage regulators to supply one or more voltages to various functional circuits and circuits within those blocks. 
     Clock Generation Circuit  105  may be configured to initialize and manage outputs of one or more clock sources. In various embodiments, the clock sources may be located in Analog/Mixed-Signal Block  104 , in Clock Generation Circuit  105 , in other blocks with IC  100 , or come from external to IC  100 , coupled through one or more I/O pins. In some embodiments, Clock Generation Circuit  105  may configure a selected clock source before it is distributed throughout IC  100 . Clock Generation Circuit  105  may include one or more clock sources. In some embodiments, Clock Generation Circuit  105  may include one or more of PLLs, FLLs, DLLs, internal oscillators, oscillator circuits for external crystals, etc. One or more clock output signals  112  may provide clock signals to various circuits of IC  100 . 
     It is noted that the IC illustrated in  FIG. 1  is merely an example. In other embodiments, a different number of circuit blocks and different configurations of circuit blocks may be possible, and may depend upon a specific application for which the IC is intended. 
     Turning to  FIG. 2 , a block diagram of a first embodiment of a clock generation circuit is illustrated. Clock generation circuit  200  may represent a component or sub-component within an integrated circuit, such as, IC  100 , for example. In the illustrated embodiment, clock generation circuit  200  includes a PLL that may be included in Clock Generation Circuit  105  in  FIG. 1 . In other embodiments, clock generation circuit  200  may include any suitable closed-loop clock signal generator circuit. An output of clock generation circuit  200 , i.e., output clock  221 , may be used as a clock source to one or more functional circuits of IC  100 , such as, for example, Processing Core  101 . Clock generation circuit  200  includes Phase Detect  201  coupled to Charge Pump  203  via PD up signal  223  and PD down signal  224 . Charge Pump  203  is coupled to low pass filter (LPF)  205 , which is, in turn, coupled to voltage controlled oscillator (VCO)  207 , which is then coupled to Frequency Divider  209 . Phase Detect  201  receives reference clock (ref clock)  220  and the output signal of the frequency divider (divider output)  222  as inputs. 
     Clock generation circuit  200  generates output clock  221  dependent upon ref clock  220 . In one embodiment, clock generation circuit  200  is programmed to generate output clock  221  at a target frequency greater than the frequency of ref clock  220 . In other embodiments, clock generation circuit  200  may be programmed to generate output clock  221  at a target frequency greater than or less than the frequency of ref clock  220 . Output clock  221  is generated by VCO  207 . Frequency Divider  209  receives output clock  221  and generates divider output  222 . Phase Detect  201  receives divider output  222  and ref clock  220 . Ref clock  220  may be generated by any suitable clock source, such as, e.g., a crystal oscillator circuit, configured to generate ref clock  220  at a known constant frequency with a desired level of accuracy. 
     Phase Detect  201  compares the phase between ref clock  220  and divider output  222 . In various embodiments, Phase Detect  201  may be referred to as a “phase detector” or “phase-frequency detector.” In some embodiments, Phase Detect  201  may determine a timing difference between the a rising and/or falling edges of ref clock  220  and divider output  222  and, generate one or more output signals dependent upon the determined timing difference. In the illustrated embodiment, Phase Detect  201  generates two output signals. PD up signal  223  is asserted high when a rising transition (also referred to as a rising edge) occurs on ref clock  220  before a corresponding rising edge on divider output  222 . A length of time that PD up signal  223  may remain asserted depends upon a time difference between the rising edge of ref clock  220  and the rising edge of divider output  222 , i.e., the phase difference between ref clock  220  and divider output  222 . If the rising edge of divider output  222  occurs after the rising edge of ref clock  220 , then the frequency of output clock  221  may be lower than the target frequency and, therefore, need to be increased. PD down signal  224  is asserted high when the rising edge occurs on divider output  222  before the corresponding rising edge of ref clock  220 . In this case, the frequency of output clock  221  may be higher than the target frequency and, accordingly, need to be decreased. 
     Charge Pump  203  receives the PD up signal  223  and PD down signal  224  from Phase Detect  201  and generates CP output signal  227  with a voltage level dependent upon the two outputs. When PD up signal  223  is asserted, then Charge Pump  203  sources current into CP output signal  227 . Conversely, when PD down signal  224  is asserted, then Charge Pump  203  sinks current from CP output signal  227 . 
     CP output signal  227  is received by LPF  205 . LPF  205 , in the illustrated embodiment, may include any suitable combination of circuit elements that allows signals with low frequencies to pass through to the output while attenuating signals with high frequencies. In various embodiments, LPF  205  may correspond to passive circuits including only capacitors and resistors, or correspond to active circuits that may include analog comparators or operational amplifiers (OpAmps) in addition to passive components. Example embodiments of low pass filters are presented later herein. 
     While the current of CP output signal  227  may change relatively quickly in response to changes in PD up signal  223  and PD down signal  224 , a voltage level of the output of LPF  205 , LPF output signal  228 , changes more slowly in comparison. In response to changes in the current sourced into or sunk from CP output signal  227 , capacitors in LPF  205  may charge or discharge respectively. In some embodiments, such as, e.g., when both PD up signal  223  and PD down signal  224  are de-asserted, a first capacitor in LPF  205  may discharge while a second capacitor receives the charge lost by the first capacitor, resulting in what is referred to herein as “charge redistribution.” 
     Due to the slower response of LPF  205 , for LPF output signal  228  to rise to a higher voltage level within a given time period, CP output signal  227  must remain at a higher voltage level for a majority of the given time period, and vice versa for the voltage level to fall to a lower voltage level. In other words, brief, high frequency pulses are filtered out of LPF output signal  228 . Accordingly, if PD up signal  223  is asserted more often than PD down signal  224  (indicating that the frequency of output clock  221  is too low), CP output signal  227  may rise to a higher voltage level, thereby causing LPF output signal  228  to rise to a higher voltage level. On the other hand, if PD down signal  224  is asserted more frequently than PD up signal  223  (indicating the frequency of output clock  221  is too high), then CP output signal  227  may fall to a lower voltage level, resulting in LPF output signal  228  to fall to a lower voltage level. 
     LPF output signal  228  is sent to VCO  207 . VCO  207  generates output clock  221  at a frequency that is dependent upon the voltage level of LPF output signal  228 . In one embodiment, a higher voltage level received by VCO  207  corresponds to a higher frequency of output clock  221  and to the contrary for lower voltage level of LPF output signal  228 . Output clock  221 , in the illustrated embodiment, is received by Frequency Divider  209 . Frequency Divider  209  generates a divided output clock signal, divider output  222 . Divider output  522  is derived from output clock  221  and dependent upon settings for Frequency Divider  209 . Settings for Frequency Divider  209  include a divisor value. In various embodiments, the divisor value may include select fractional values, integer values within a predetermined range, or a subset of integers, such as, for example, powers of two (1, 2, 4, 8 . . . ). Divider output  222  is generated with a frequency equal to the frequency of output clock  221  divided by the divisor value. Subsequently, when clock generation circuit  200  is locked and divider output  222  has a frequency equal to ref clock  220 , the frequency of output clock  221  is equal to the frequency of ref clock  220  multiplied by the divisor value. 
     In the illustrated embodiment, clock generation circuit  200  is in a locked state once corresponding edges of ref clock  220  and divider output  222  occur within a predetermined amount of time of one another. Consequently, ref clock  220  and divider output  222  may not have exactly equal frequencies during the locked state. The predetermined amount of time, and, therefore, the accuracy of output clock  221 , may be determined during design of clock generation circuit  200  to establish an acceptable level of accuracy for intended uses of output clock  221 . 
     It is noted that the embodiment of clock generation unit  200  as illustrated in  FIG. 2  is merely an example. The illustration of  FIG. 2  has been simplified to highlight features relevant to this disclosure. Various embodiments may include different configurations of the circuit bocks, including additional circuit blocks. Furthermore, although a PLL is used in the examples, the features described may apply to any suitable embodiment of a closed loop clock generation unit, such as, e.g., a DLL. 
     Moving to  FIGS. 3 and 4 ,  FIG. 3  shows a timing diagram including possible waveforms associated with an embodiment of clock generation circuit  200  presented in  FIG. 2 . The waveforms of timing diagram  300  illustrate voltage or logic levels versus time for various signals shown in  FIG. 2 . Referring collectively to  FIG. 2  and  FIG. 3 , timing diagram  300  includes waveforms ref clock  301 , output clock  302 , divider output  303 , PD up signal  304 , and PD down signal  305 .  FIG. 4  illustrates a chart representing frequency of output clock  222  versus time. Chart  400  includes waveforms target frequency  401  and output clock  402 . The waveforms in  FIGS. 3 and 4  may correspond to the similarly named signals in  FIG. 2 . It is noted that both output clock  302  and output clock  402  correspond to output clock  521 . 
     Referring collectively to clock generation circuit  200 , timing diagram  300 , and chart  400 , the signals begin at t 0 . At time t 0 , all signals are low. The frequency of output clock  402  is lower than target frequency  401 . The frequency of output clock  402  may be lower than target frequency  401  for various reasons, such as, for example, Clock Generation Circuit  500  may have been recently enabled after a reset or power on event. 
     At time t 1 , a rising edge occurs on both ref clock  301  and divider output  303 . In the illustrated embodiment, both PD up signal  304  and PD down signal  305  briefly transition high and then return to a logic low. In other embodiments, only one of PD up signal  304  and PD down signal  305  may transition high, or neither may transition. At the next rising edge of ref clock  301 , divider output  303  remains high and as a result, PD up signal  304  transitions high while PD down signal  305  remains low. This high value on PD up signal  304  and low value on PD down signal  305  may cause Charge Pump  203  to source current to its output, thereby charging capacitors within LPF  205 . The charging capacitors in LPF  205  cause a corresponding increase in the voltage level of LPF output signal  228 , which, in turn, causes VCO  207  to increase the frequency of output clock  402 , as shown in chart  400 . 
     PD up signal  304  remains high until the next rising edge of divider output  303  at time t 2 , at which time PD down signal  305  briefly transitions high, causing both PD up signal  304  and PD down signal  305  to transition low. The low values of both PD up signal  304  and PD down signal  305  may cause Charge Pump  203  to cease sourcing current to LPF  205 . Due to the sudden loss of current from Charge Pump  203 , capacitors in LPF  205  enter a charge redistribution state which causes the voltage level of LPF output signal  228  to fall. This fall in the voltage level of LPF output signal  228  may result in a corresponding reduction in the frequency of output clock  402 . 
     The next rising edge of ref clock  301  at time t 3  causes PD up signal  304  to transition high, again resulting in current being sourced from Charge Pump  203  to LPF  205 . As LPF  205  receives the charge, the voltage level of LPF output signal  228  increases, thereby causing increases in the frequencies of output clock  402  and divider output  303 . 
     At time t 4 , another rising edge occurs on divider output  303 , causing PD down signal  305  to transition high. The transition on PD down signal  305  causes both PD up signal  304  and PD down signal  305  to transition low again. As a result, Charge Pump  203  again ceases charging of LPF  205  which again leads to charge redistribution in LPF  205  and a corresponding reduction in the frequency of output clock  402 . 
     The next rising edge of ref clock  301  at time t 5  results in PD up signal  304  transitioning high again, resulting in Charge Pump  203  resuming charging of LPF  205 . The voltage level of LPF output signal  228  increases, resulting in an increase in the frequency of output clock  302 . By time t 6 , both ref clock  301  and divider output  303  are running at similar frequencies. Neither PD up signal  304  nor PD down output  304  may transition high for very long, and clock generation circuit  200  may be considered locked. 
     It is noted that in the example of  FIGS. 3 and 4 , that the frequency of output clock  402  increases in increments, with periods of decreasing frequency when both PD up signal  304  and PD down signal  305  are low. These periods when output clock  402  decreases may correspond to occurrences of cycle slip causing charge redistribution. Occurrences of cycle slip may contribute to delays in clock generation circuit  200  reaching a locked state. 
     It is also noted that timing diagram  300  of  FIG. 3  and chart  400  of  FIG. 4  merely illustrate examples of signals resulting from one embodiment of clock generation circuit  200 . The signals are simplified to provide clear descriptions of the disclosed concepts. In various embodiments, the signals may appear different due various influences such as technology choices for building the circuits, actual circuit design and layout, ambient noise in the environment, choice of power supplies, etc. Additionally, the relationship between times t 0  through t 6  between  FIG. 3  and  FIG. 4  are not intended to be to scale. In other embodiments, changes in the frequency of output clock  302 ( 402 ) may occur at different rates than illustrated. 
     Turning now to  FIG. 5  a block diagram of a second embodiment of a clock generation circuit is shown. Clock Generation Circuit  500  may be included in Clock Generation Circuit  105  in  FIG. 1 . Clock Generation Circuit  500  includes Phase Detect  501  coupled to switch (SW)  513  via PD up signal  523  and to switch (SW)  514  via PD down signal  524 . Both switch  513  and switch  514  are coupled to Charge Pump  503  which is then coupled to low pass filter (LPF)  505 . LPF  505  is coupled to voltage controlled oscillator (VCO)  507 , which is then coupled to Frequency Divider  509 . An output of Frequency Divider  509  (divider output  522 ) is coupled to switch (SW)  512 . Frequency Monitor  510  is coupled to OR gate  511  and switches (SW)  513  and  514 . OR gate  511  is coupled to switch (SW)  512  and Frequency Divider  509 . Clock Generation Circuit  500  receives reference clock (ref clock)  520  as an input to Phase Detect  501  and generates output clock  521  from VCO  507 . In the illustrated embodiment, the circuit blocks in  FIG. 5  operate as described above in regards to the similarly named circuit blocks in  FIG. 2 , except as noted below. 
     In the illustrated embodiment, Frequency Monitor  510  receives output clock  521  and ref clock  520 . Frequency Monitor  510  compares a frequency of output clock  521  to a frequency of ref clock  520 . In some embodiments, Frequency Monitor  510  includes a counter circuit and increments a count value for each detected rising edge of output clock  521  beginning at a start of a comparison cycle. In some embodiments, this count value is captured and then reset upon detecting an end of the comparison cycle. In other embodiments, the count value may continue to increment while a previously captured count value is subtracted from the current count value to determine a number of clock edges detected during the most recent comparison cycle. In various embodiments, a comparison cycle may correspond to one period of ref clock  520 , or multiple cycles of ref clock  520 . Periods of ref clock  520  may be determined by detecting rising or falling edges of ref clock  520 . 
     Although a counter circuit is included in the illustrated embodiment, Frequency Monitor  510  may be implemented using any suitable circuit. For example, in other embodiments, Frequency Monitor  510  may include delay circuits, and/or frequency filters. 
     Depending on settings for clock generation circuit  500 , output clock  521  runs at a frequency that is a certain multiple of ref clock  520 . If the count value remains below a first threshold value for a complete comparison cycle, then the frequency of output clock  521  may be lower than a target frequency. If the count value increases above a second threshold value within a comparison cycle, then the frequency of output clock  521  may be higher than the target frequency. If the count value is between the first and second thresholds for a comparison cycle, then the frequency of output clock  521  may be within a predetermined range of the target frequency. 
     For example, Clock Generation Circuit  500  may be set to generate output clock  521  at a frequency 32 times higher than ref clock  520 . In such an embodiment, Frequency Monitor  510  would be expected to count approximately 32 rising edges (or falling edges in other embodiments) of output clock  521  during a complete comparison cycle, when clock generation circuit is operating in a locked state. In such an example, the first threshold value may be set at 26 and the second threshold set at 38. 
     Frequency Monitor  510 , in one embodiment, asserts FM1 control signal  525  when the count value is reset and the count value for a comparison cycle is below the first threshold value. In some embodiments, Frequency Monitor  510  asserts FM2 control signal  526  if the count value exceeds the second threshold value. If the count value falls between the first and second threshold values for a comparison cycle, then the control signals are de-asserted. 
     When FM1 control signal is asserted, switches  512  and  514  are opened and switch  513  remains closed. Opening switch  512 , via the output of OR  511 , decouples Phase Detect  501  from Frequency Divider  509 , such that Phase Detect  501  receives ref clock  520  but not divider output  522 . Operation of Clock Generation Circuit  500  with switch  512  open is referred to herein as an “open-loop mode of operation,” or simply “open-loop mode.” As a result of being decoupled from divider output  522 , Phase Detect  501  asserts PD up signal  523 . PD up signal  523  may remain asserted for as long as FM1 control signal  525  remains asserted. The assertion of PD up signal  523  may cause Charge Pump  503  to charge LPF  505 , driving LPF output signal  528  to a high voltage level causing, in turn, VCO  507  to generate output clock  521  at ever increasing frequencies. 
     Output clock  521  eventually reaches a high enough frequency to cause the count value in Frequency Monitor  510  to exceed the first threshold value (while remaining below the second threshold value) and, subsequently, cause Frequency Monitor  510  to de-assert FM1 control signal  525 . In response to the de-assertion of FM1 control signal  525 , switches  512  and  514  are closed and Clock Generation Circuit  500  may operate as described in regards to clock generation circuit  200  in  FIG. 2 . Operation of Clock Generation Circuit  500  with switch  512  closed is referred to herein as a “closed-loop mode of operation,” or simply “closed-loop mode.” 
     In the illustrated embodiment, when FM2 control signal  526  is asserted, switches  512  and  513  are opened and switch  514  remains closed. Phase Detect  501  generates a high signal on PD down signal  524  causing Charge Pump  503  to discharge LPF  505 , which causes the voltage level of LPF output  528  to fall. The falling voltage level of LPF output  528  is received by VCO  507 , resulting in VCO  507  generating output clock  521  at gradually lower frequencies. Once the frequency of output clock  521  falls to a point that the count value in Frequency Monitor  510  is between the first and second threshold values, FM2 control  526  is de-asserted and switches  512  and  513  are closed. Clock Generation Circuit  500  may return to operating as described for clock generation circuit  200 . 
     In some embodiments, while either FM1 control signal  525  or FM2 control signal  526  are asserted, Frequency Divider  509  may be placed into a reduced power mode or disabled to reduce power consumption, as indicated by the shading in  FIG. 5 . Since divider output  522  is decoupled from Phase Detect  501  while either control signal is asserted, operation of Frequency Divider  509  is not being used and may be halted to conserve power. 
     It is noted that by monitoring the frequency of output clock  521  and influencing the signals received by VCO  507 , an amount of time used for acquiring lock from an unlocked state may be reduced. In the embodiment of Clock Generation Circuit  500 , inputs to Charge Pump  503  are controlled to influence the input to VCO  507 . 
     It is also noted that  FIG. 5  is merely an example of a clock generation circuit. Other methods of monitoring a clock frequency than described for Frequency Monitor  510  may be utilized in other embodiments. 
     Moving now to  FIGS. 6 and 7 ,  FIG. 6  depicts a timing diagram including possible waveforms associated with an embodiment of a clock generation circuit, such as, e.g., Clock Generation Circuit  500  in  FIG. 5 . In the illustrated embodiment, timing diagram  600  and chart  700  include waveforms associated with ref clock  520 , output clock  521 , divider output  522 , PD up signal  523 , PD down signal  524 , and FM1 control signal  525 . Similar to timing diagram  300  in  FIG. 3 , the waveforms of timing diagram  600  illustrate voltage or logic levels versus time and include ref clock  601 , output clock  602 , divider output  603 , PD up signal  604 , PD down signal  605 , and FM1 control signal  606 .  FIG. 7  illustrates a chart representing frequency versus time. Chart  700  includes waveforms target frequency  701  and output clock  702 . The waveforms in  FIGS. 6 and 7  may correspond to the similarly named signals in  FIG. 5 . It is noted that both output clock  602  and output clock  702  correspond to output clock  521 , with  602  showing voltage versus time and  702  illustrating frequency versus time. 
     Referring collectively to clock generation circuit  500 , timing diagram  600 , and chart  700 , the signals begin at t 0 . In the illustrated embodiment, Clock Generation Circuit  500  receives settings to generate output clock  702  at target frequency  701 . At time t 0 , all signals are low. The frequency of output clock  702  is much lower than target frequency  701 . The frequency of output clock  702  may be lower than target frequency  701  for various reasons, such as, for example, one or more settings for Clock Generation Circuit  500  may have been recently changed to increase the frequency of output clock  702 . 
     At time t 1 , a rising edge occurs on ref clock  601 . In one embodiment, the rising edge of ref clock  601  may correspond to an end of a comparison cycle in Frequency Monitor  510 . The count value is below the first threshold value, as described above in regards to  FIG. 5 , which corresponds to output clock  702  running at a lower frequency than target frequency  701 . In response to the determination that that output clock  702  is running at too low of a frequency, Frequency Monitor  510  assert FM1 control signal  606  which decouples divider output  603  from Phase Detect  501  by opening switch  512 . In addition, switch  514  may be opened to decouple Charge Pump  503  from PD down signal  524 . In the illustrated example, divider output  603  did not transition high before being decoupled from Phase Detect  501 , PD up signal  604  transitions high in response to the rising edge of ref clock  601 . 
     While FM1 control signal  606  is asserted, Clock Generation Circuit  500  operates in open-loop mode. In open-loop mode, divider output  603  is decoupled from Phase Detect  501 , and PD up signal  604 , therefore, remains asserted as Phase Detect  501  is isolated from rising edges generated by Frequency Divider  509 . In some embodiments, as previously described, Frequency Divider  509  may be disabled or powered down while FM1 control signal  606  is asserted. Frequency Monitor  510  continues to monitor output clock  602 . The asserted value of PD up signal  604  causes Charge Pump  503  to gradually charge LPF  505 . LPF  505  subsequently increases the voltage level of its output signal to VCO  507 , resulting in the frequency of output clock  602 ( 702 ) to increase over time, as shown between time t 1  and time t 2  in both timing diagram  600  and chart  700 . It is noted that while referred to herein as “open-loop” mode while FM1 control signal  606  is asserted, Phase Detect  501  receives feedback via Frequency Monitor  510 , in what may be considered an alternate feedback closed-loop. For the purposes of this disclosure, “open-loop” mode includes modes in which feedback is received via Frequency Monitor  510  and “closed-loop” mode refers to modes of operation in which feedback is received via Frequency Divider  509 . 
     A rising edge on ref clock  601  at time t 2 , in the illustrated embodiment, may signal an end to a comparison cycle in which the count value is greater than the first threshold value and less than the second threshold value, indicating that the frequency of output clock  702  is within a predetermined range of target frequency  701 . Frequency Monitor  510 , in response to this indication, de-asserts FM1 control signal  606 . The de-assertion of FM1 control signal  525  caused switches  512  and  514  to close, putting Clock Generation Circuit  500  into closed-loop mode. Frequency Divider  509  generates divider output  603 , which is now coupled to Phase Detect  501 . In closed-loop mode, operation of Clock Generation Circuit  500  may correspond to the description of clock generation circuit  200  in  FIG. 2  with the exception that since the frequency of output clock  602  is within the predetermined range of target frequency  701 , cycle slips may be avoided. 
     It is noted that in the example of  FIG. 7 , that the frequency of output clock  702  increases more consistently than is shown for output clock  402  in  FIG. 4 . In the example of  FIG. 7 , no instances of cycle slip are illustrated which may contribute to a decreased amount of time for Clock Generation Circuit  500  to reach a locked state. 
     It is also noted that timing diagram  600  of  FIG. 6  and chart  700  of  FIG. 7  are examples of possible signals resulting from one embodiment of clock generation circuit  500 . The signals are simplified to clearly demonstrate the disclosed concepts. For example, the frequency of output clock  602  is not intended to be in scale with ref clock  601  or divider output  603 . In addition, the relationship between times t 0  through t 4  between  FIG. 3  and  FIG. 4  are not intended to be to scale. In other embodiments, changes in the waveforms of output clock  602  and  702  may occur at different rates than illustrated. 
     Turning to  FIG. 8 , an example circuit for an embodiment of a charge pump and low pass filter is illustrated. Charge pump  803  and low pass filter (LPF)  805 , in the illustrated embodiment, are part of a closed loop clock circuit, such as, for example, Clock Generation Circuit  900  in  FIG. 9 , described below. Charge Pump  803  includes Current Source  811 , Current Sink  812 , OR logic gates (OR)  814  and  815 , and switches (SW)  816  and  817 . Charge Pump  803  receives input signals PD up signal  823 , PD down signal  824 , FM1 control signal  825 , and FM2 control signal  826 , and generates CP output signal  827  dependent upon the received input signals. Low pass filter (LPF)  805  includes resistor (R)  813  and capacitors (C)  818  and  819 . LPF  805  receives CP output  827  and generates LPF output  828 . 
     In the illustrated embodiment, Charge Pump  803  operates by coupling Current Source  811  and decoupling Current Sink  812  from CP output  827  to increase an amount of charge provided to LPF  805 . The charge is stored in C  818  and C  819 , thereby increasing a voltage level of LPF output  828 . While accumulating charge, the voltage level across C  818  may be lower than across C  819  due to a voltage drop across R  813 . When CP output  827  remains at a constant voltage level, the voltage level across C  818  may reach the voltage level across C 819  as both capacitors reach their respective charge capacity. It is noted that, in the illustrated embodiment, CP output  827  and LPF output  828  are signals on a same node, and therefore, are equivalent signals. 
     Current Source  811  is decoupled and Current Sink  812  coupled to LPF  805  to decrease the amount of charge stored in C  818  and C  819 , thereby lowering the voltage level of LPF output  828 . While discharging via Current Sink  812 , the voltage level across C  819  may fall faster than across C  818 , again due to R  813 . In one embodiment, during operation of the clock generation circuit, C  819  stores and releases charge faster than C  818 . At some points in time, charge from C  819  may be provided to C  818 , and vice versa at other points in time. The faster this redistribution of charge occurs, the faster the clock generation circuit may be able to achieve lock. 
     Input signals PD up signal  823  and FM1 control signal  825 , in the illustrated embodiment, are received by OR  814  to generate a control signal for SW  816 . When closed, SW  816  couples Current Source  811  to LPF  805 . Assertion of either PD up signal  823  or FM1 control signal  825 , therefore, causes the voltage level of CP output  827  to increase. De-assertion of both PD up signal  823  and FM1 control signal  825 , on the other hand, decouples Current Source  811  from LPF  805 , disabling charging of C  818  and C  819 . 
     Similarly, input signals PD down signal  824  and FM2 control signal  826  are received by OR  815  to generate a control signal for SW  817 . SW  817  couples Current Sink  812  to LPF  805  when closed and decouples Current Sink  812  from LPF  805  when open. Consequently, assertion of either PD down signal  824  or FM2 control signal  826  causes the voltage level of CP output  827  to decrease, while de-assertion of both PD down signal  824  and FM2 control signal  826  decouples Current Sink  812  from LPF  805 , thereby discharging or disabling discharging, respectively, of C  818  and C  819 . 
     In some embodiments, Current Source  811  and SW  816  may be implemented as a single transistor, or other type of transconductance device. Current Sink  812  and SW  817  may be similarly implemented. 
     It is noted that Charge Pump  803  and LPF  805  are merely examples of a charge pump circuit and low pass filter circuit, respectively. In other embodiments, various circuit changes may be employed. For example, in one embodiment, switches SW  816  and SW  817  may be removed and current sources  801  and  802  may receive control signals directly. 
     Moving to  FIG. 9 , a block diagram of a third embodiment of a clock generation circuit is shown. In various embodiments, Clock Generation Circuit  900  may be included in Clock Generation Circuit  105  in  FIG. 1 . Clock Generation Circuit  900  includes Phase Detect  901  coupled to Charge Pump  903 , which is coupled to low pass filter (LPF)  905 . LPF  905  is coupled to voltage controlled oscillator (VCO)  907 , which is then coupled to Frequency Divider  909  and Frequency Monitor  910 . An output of Frequency Divider  909  (divider output  922 ) is coupled to Phase Detect  901 . Two outputs of Frequency Monitor  910  (FM1 control signal  925  and FM2 control signal  926 ) are received by OR gate (OR)  911 , the output of which is coupled to Phase Detect  901  and Frequency Divider  909 . Clock Generation Circuit  900  receives reference clock (ref clock)  920  as an input to Phase Detect  901  and generates output clock  921  from VCO  907 . 
     In the illustrated embodiment, Clock Generation Circuit  900  includes functional circuits that are similar to similarly named and numbered circuits in clock generation circuit  200  in  FIG. 2 . Functional descriptions of common circuits may be as described above in regards to  FIG. 2 , except where noted below. Clock Generation Circuit  900  may operate in both open-loop and closed-loop modes. When operating in the closed-loop mode, operation is similar the description of clock generation circuit  200 . 
     Frequency Monitor  910 , in one embodiment, generates a count value by counting a number of rising or falling edges of output clock  921  during a comparison cycle. Similar to Frequency Monitor  510  in  FIG. 5 , a comparison cycle may be determined by one or more periods of ref clock  920 . Frequency Monitor  910  asserts output signals FM1 control signal  925  or FM2 control signal  926  depending on if the count value, upon completion of a comparison cycle, is below a first threshold value, or above a second threshold value. Neither FM1 control signal  925  nor FM2 control signal  926  may be asserted if the count value is between the first and second threshold values. As described above in regards to Frequency Monitor  510 , Frequency Monitor  910  may be implemented with any suitable circuit. 
     Charge Pump  903  receives FM1 control signal  925  and FM2 control signal  926  from Frequency Monitor  910 . In some embodiments, Charge Pump  903  corresponds to charge Pump  803  in  FIG. 8 . While Clock Generation Circuit  900  operates in closed-loop mode, FM1 control signal  925  and FM2 control signal  926  are both de-asserted and Charge Pump  903  adjust the current sourced or sunk on CP output  927  dependent upon PD up signal  923  and PD down signal  924  generated by Phase Detect  901 . 
     If the frequency of output clock  921  is below the first threshold value or above the second threshold value, then either FM1 control signal  925  or FM2 control signal  926  is asserted, respectively, and the output of OR  911  is asserted. In response to the assertion, Phase Detect  901  and/or Frequency Divider  909 , as indicated by the shaded boxes in  FIG. 9 , may be disabled or powered down, and Clock Generation Circuit  900  may operate in open-loop mode. In open-loop mode, Charge Pump  903  sources current to LPF  905  if FM1 control signal  925  is asserted, or sinks current from LPF  905  if FM2 control signal  926  is asserted. The sourcing or sinking of current causes LPF  905  and VCO  907  to respond as previously described in regards to  FIGS. 2 and 5 , and the frequency of output clock  921  may increase or decrease until the count value in Frequency Monitor  910  is between the first and second threshold values. In response to the count value being between the threshold values, both FM1 control signal  925  and FM2 control signal  926  may be de-asserted, causing the output of OR  911  to de-assert, and in turn, causing Phase Detect  901  and Frequency Divider  909  to be enabled, placing Clock Generation Circuit  900  back into closed-loop mode. 
     Waveforms for the signals of Clock Generation Circuit  900  when output clock signal  921  is below the first threshold value may be similar to the waveforms of  FIGS. 6 and 7 . Waveforms for PD up signal  923  and PD down signal  924 , however, may differ from those shown in  FIG. 6  during the time period between t 1  and t 2 . 
     It is noted that OR gates are used in the illustrated embodiments, and represent one type of logic circuit. In other embodiments, other types of logic gates may be utilized. 
     It is noted that  FIG. 9  is one example of a clock generation circuit. Other methods of monitoring a clock frequency than described for Frequency Monitor  510  may be utilized in other embodiments. For example, rather than counting up towards threshold values, other embodiments of frequency monitors may count down. 
     Turning now to  FIG. 10 , another example circuit for an embodiment of a low pass filter is depicted. In one embodiment, Low Pass Filter  1000  includes capacitor C  1019  coupled in parallel with resistor R  1013  and capacitor C  1018 . Switch SW  1005  is coupled in parallel with R  1013 , and is operated by an output of OR logic gate (OR)  1011 . Low pass filter  1000  receives input signals CP output  1027 , FM1 control signal  1025 , and FM2 control signal  1026 . Low pass filter  1000  generates LPF output signal  1028  dependent upon the received input signals. 
     In the illustrated embodiment, when SW  1005  is open, Low Pass Filter  1000  operates similar to the description provided above regarding LPF  805  in  FIG. 8 . When FM1 control signal  1025  or FM2 control signal  1026  is asserted, the output of OR  1011  is asserted and SW 1005  is closed. With SW  1005  closed, R  1013  is bypassed and C  1018  and C  1019  are driven to a same voltage level across their respective terminals. Current received via CP output  1027  charges both C  1018  and C  1019  such that the voltage level across their respective terminals remains equal. Charge is stored by each capacitor based on the respective capacitance value. For example, if both C  1018  and C  1019  have equal capacitance values, then each capacitor will store charge CP output  1027  at substantially the same rate. 
     As described for LPF  805 , a change in current from CP output  1027  may result in charge redistribution between C  1018  and C  1019  when SW  1005  is open. By closing SW  1005  in response to an assertion of FM1 control signal  1025  or FM2 control signal  1026 , any charge redistribution between C  1018  and C  1019  may occur faster than if SW  1005  remains open. Voltage level changes to the voltage level across C  1019  that are caused by a change in the current from CP output  1027  may also occur faster with SW  1005  closed, thereby resulting LPF output  1028  reacting faster than when SW  1005  is open. 
     In some embodiments, the aforementioned component values of C 1018 , C  1019 , and R  1013  may be selected to achieve a desired cutoff frequency for LPF output  1028 . As used herein, “cutoff frequency” corresponds to a frequency value at which Low Pass Filter  1000  attenuates LPF output  1028 . For example, if Low Pass Filter  1000  is designed for a cutoff frequency of 100 kilohertz (kHz), then changes in current from CP output signal  1027  occurring at frequencies below 100 kHz may pass through to LPF output  1028 , while frequencies of above 100 kHz may be attenuated. Generally speaking, the higher the frequency of changes on CP output signal  1027  is above the cutoff frequency, the less of CP output signal  1027  is passed through to LPF output signal  1028 . 
     It is noted that low pass filter  1000  is an example circuit for demonstrating the disclosed concepts. Additional components may be included in some embodiments. Other suitable low pass filter designs may be utilized in other embodiments. 
     Moving now to  FIG. 11 , a block diagram of a fourth embodiment of a clock generation circuit is shown. In various embodiments, Clock Generation Circuit  1100  may be included in Clock Generation Circuit  105  in  FIG. 1 . Clock Generation Circuit  1100  includes Phase Detect  1101  coupled to Charge Pump  1103  which is then coupled to low pass filter (LPF)  1105 . LPF  1105  is coupled to voltage controlled oscillator (VCO)  1107 , which is then coupled to Frequency Divider  1109  and Frequency Monitor  1110 . An output of Frequency Divider  1109  (divider output  1122 ) is coupled to Phase Detect  1101 . Two outputs of Frequency Monitor  1110  (FM1 control signal  1125  and FM2 control signal  1126 ) are coupled to OR gate (OR)  1111 . Clock Generation Circuit  1100  receives reference clock (ref clock)  1120  as an input to Phase Detect  1101  and generates output clock  1121  from VCO  1107 . 
     Clock Generation Circuit  1100  includes functional circuits that are similar to similarly named and numbered circuits in Clock Generation Circuit  900  in  FIG. 9 . Functional descriptions of common circuits may be as described above in regards to  FIG. 9 , except where noted below. Similar to clock generation circuit  900 , Clock Generation Circuit  1100  may operate in both open-loop and closed-loop modes. When operating in the closed-loop mode, operation is similar the description of clock generation circuit  900 . 
     Frequency Monitor  1110 , in the illustrated embodiment, generates a count value as described for Frequency Monitor  910  in  FIG. 9 . Frequency Monitor  1110  asserts output signals FM1 control signal  1125  or FM2 control signal  1126  depending on if the count value, upon completion of a comparison cycle, is below a first threshold value, or above a second threshold value. Neither FM1 control signal  1125  nor FM2 control signal  1126  may be asserted if the count value is between the first and second threshold values. 
     LPF  1105 , in one embodiment, corresponds to low pass filter  1000  in  FIG. 10 . When Frequency Monitor  1110  asserts FM1 control signal  1125  or FM2 control signal  1126 , SW  1005  in LPF  1105  is closed, thereby allowing charge redistribution to occur faster between C  1018  and C  1019 . The voltage level of LPF output  1128  reacts quickly to changes in the current from CP output  1127 . VCO  1107  receives LPF output  1128  and increases or decreases the frequency of output clock  1121  in response to respective increases and decreases in the voltage level of LPF output  1128 . 
     Additionally, assertion of FM1 control signal  1125  or FM2 control signal  1126  may cause one or more of Phase Detect  1101 , Charge Pump  1103 , and Frequency Divider  1109 , as indicated by the shading in  FIG. 11 , to enter reduced power modes or to be disabled. If Charge Pump  1103  is placed in a reduced power mode or disabled, then CP output  1127  may be held at a high voltage level, such as, for example, by using a pull-up device to couple CP output  1127  to a power supply node such as VDD. 
     Waveforms for the signals of Clock Generation Circuit  1100  when output clock signal  1121  is below the first threshold value may be similar to the waveforms of  FIGS. 6 and 7 . Waveforms for PD up signal  1123  and PD down signal  1124 , however, may differ from those shown in  FIG. 6  during the time period between t 1  and t 2 . 
     It is noted that Clock Generation Circuit  1100  is an example embodiment, and other variations are contemplated. In other embodiments, for example, OR gate  1111  may be omitted and both FM1 control signal  1125  and FM2 control signal  1126  may be received by Phase Detect  1101 , Charge Pump  1103  and Frequency Divider  1109 . 
     Turning to  FIGS. 12 and 13 ,  FIG. 12  shows a third timing diagram illustrating possible waveforms of an embodiment of a clock generation circuit such as, e.g., Clock Generation Circuit  500  in  FIG. 5 . In the illustrated embodiment, timing diagram  1200  and chart  1300  include waveforms associated with ref clock  520 , output clock  521 , divider output  522 , PD up signal  523 , PD down signal  524 , and FM2 control signal  526 . Similar to timing diagram  600  in  FIG. 6 , the waveforms of timing diagram  1200  illustrate voltage or logic levels versus time and include ref clock  1201 , output clock  1202 , divider output  1203 , PD up signal  1204 , PD down signal  1205 , and FM1 control signal  1206 .  FIG. 13  depicts a chart representing frequency versus time. Chart  1300  includes waveforms target frequency  1301  and output clock  1302 . The waveforms in  FIGS. 12 and 13  may correspond to the similarly named signals in  FIG. 5 . It is noted that both output clock  1202  and output clock  1302  correspond to output clock  521 , with  1202  showing voltage versus time and  1302  illustrating frequency versus time. 
     Referring collectively to clock generation circuit  500 , timing diagram  1200 , and chart  1300 , the signals begin at t 0 . Clock Generation Circuit  500  may receive new settings to generate output clock  1302  at target frequency  1301 , which is lower than a current frequency of output clock  1302 . At time t 0 , all signals are low and the frequency of output clock  1302  is higher than target frequency  1301 . 
     At time t 1 , a rising edge occurs on ref clock  1201 . In the illustrated embodiment, the rising edge of ref clock  1201  may correspond to an end of a comparison cycle in Frequency Monitor  510 . The count value is above the second threshold value, which corresponds to output clock  1302  running at a higher frequency than target frequency  1301 . In response to this determination that that output clock  1302  is running at too high of a frequency, Frequency Monitor  510  assert FM2 control signal  1206  which causes divider output  1203  to be decoupled from Phase Detect  501  by opening switch  512 . In addition, switch  513  may be opened to decouple Charge Pump  503  from PD up signal  523 . In the illustrated example, divider output  1203  did not transition high before being decoupled from Phase Detect  501 , PD down signal  1205  transitions high in response to the rising edge of ref clock  1201 . 
     While FM2 control signal  1206  is asserted, Clock Generation Circuit  500  operates in open-loop mode with divider output  1203  decoupled from Phase Detect  501 . PD down signal  1205 , therefore, remains asserted as Phase Detect  501  is isolated from rising edges generated by Frequency Divider  509 . In some embodiments, as previously described, Frequency Divider  509  may be disabled or powered down while FM2 control signal  1206  is asserted. Frequency Monitor  510  continues to monitor output clock  1202 . The asserted value of PD down signal  1205  causes Charge Pump  503  to gradually decrease the voltage level of its output to LPF  505 . LPF  505  subsequently decreases the voltage level of its output signal to VCO  507 , resulting in the frequency of output clock  1202 ( 1302 ) to decrease over time, as shown between time t 1  and time t 2  in both timing diagram  1200  and chart  1300 . 
     In the illustrated embodiment, a rising edge on ref clock  1201  at time t 2  may signal an end to a comparison cycle in which Frequency Monitor  510  determines that the count value is greater than the first threshold value and less than the second threshold value, indicating that the frequency of output clock  1302  is within a predetermined range of target frequency  1301 . Frequency Monitor  510 , in response to this indication, de-asserts FM2 control signal  1206 . The de-assertion of FM2 control signal  1206  causes switches  512  and  513  to close, placing Clock Generation Circuit  500  into closed-loop mode. Frequency Divider  509  generates divider output  1203 , which is now coupled to Phase Detect  501 . In closed-loop mode, operation of Clock Generation Circuit  500  may correspond to the description of clock generation circuit  200  in  FIG. 2  with the exception that since the frequency of output clock  602  is within the predetermined range of target frequency  1301 , cycle slips may be avoided. 
     It is noted that in the example of  FIG. 13 , that the frequency of output clock  702  decreases smoothly. In the example of  FIG. 13 , no instances of cycle slip are illustrated, which may contribute to a decreased amount of time for Clock Generation Circuit  500  to reach a locked state. 
     It is also noted that timing diagram  1200  of  FIG. 12  and chart  1300  of  FIG. 13  are examples of signals resulting from an embodiment of clock generation circuit  500 . The waveforms of  FIGS. 12 and 13  may also correspond to other embodiments, such as, for example, Clock Generation Circuit  900  and Clock Generation Circuit  1100 . In these other embodiments, some signals, e.g., PD up  1204  and PD down  1205 , may differ from the waveforms shown. The illustrated signals are simplified for demonstrative purposes. For example, the frequency of output clock  1202  is not intended to be in scale with ref clock  1201  or divider output  1203 . 
     Moving to  FIG. 14 , a flow diagram of an embodiment of a method for operating a closed-loop clock generation circuit is illustrated. The method may be applied to a clock generation circuit, such as, for example, Clock Generation Circuit  500  in FIG.  5 , Clock Generation Circuit  900  in  FIG. 9 , or Clock Generation Circuit  1100  in  FIG. 11 . Referring collectively to Clock Generation Circuit  500  and method  1400  in  FIG. 14 , the method may begin in block  1401 . 
     A clock signal is generated (block  1402 ). Clock Generation Circuit  500 , for example, may transition from a disabled state to an enabled state, in which case VCO  507  may begin generating output clock  521  with a default frequency. In other examples, Clock Generation Circuit  500  may be currently generating output clock  521  at a first frequency and then receive updated settings for generating output clock  521  at a second frequency. The frequency of output clock  521  may be determined by a voltage level of a control signal received by VCO  507 , such as, e.g., LPF output  528  in the embodiment of  FIG. 5 . 
     Further operation of method  1400  may depend upon a frequency of the clock signal and a first threshold value (block  1404 ). In the illustrated embodiment of  FIG. 5 , Frequency Monitor  510  receives output clock  521  and measures its frequency in relation to a reference clock signal (ref clock  520 ). In one embodiment, Frequency Monitor  510  measures the frequency of output clock  521  by counting its rising or falling edges that occur between two rising or falling edges of ref clock  520 . The two edges of ref clock  520  may indicate a beginning and an end to a given comparison cycle. In various embodiments, Frequency Monitor  510  may use a single period or multiple periods of ref clock  520  as a comparison cycle. The first threshold value may correspond to a lower frequency limit for Clock Generation Circuit  500  to operate in a closed-loop mode. The frequency of output clock  521  being lower than the first threshold value may indicate that Clock Generation Circuit  500  should operate in open-loop mode to reduce a time to acquire lock by increasing the frequency of output clock  521  more quickly than may be accomplished in closed-loop mode. If the frequency of output clock  521  is less than the first threshold value, then the method moves to block  1408  to adjust a control signal. Otherwise, the method moves to block  1410  to compare output clock  521  to a second threshold value. 
     If the frequency of the clock signal is less than the first threshold, then the control signal is adjusted based on the measured frequency of the clock signal (block  1408 ). Frequency Monitor  510  asserts FM1 control signal  525  if the frequency of output clock  521  is less than the first threshold. The assertion of FM1 control signal  525  causes Clock Generation Circuit  500  to operate in an open-loop mode. Open-loop mode operation may be enabled in different ways in various embodiments. For example, in the embodiment of  FIG. 5 , the assertion of FM1 control signal  525  results in divider output  522  being decoupled from Phase Detect  501  and PD down signal  524  being decoupled from Charge Pump  503 . With divider output  522  decoupled, Phase Detect  501  asserts PD up signal  523 , which is received by Charge Pump  503 . Charge Pump  503  sources current through CP output signal  527  to LPF  505 . The received charge in LPF  505  increases a voltage level of LPF output signal  528  which is received at a control input to VCO  507 . The increased voltage level of LPF output signal  528  at the control input of VCO  507  causes VCO  507  to increase the frequency of output clock  521 . The method may return to block  1404  to continue monitoring the clock signal. 
     If, in block  1404 , it is determined that the frequency of the clock signal is less than the first threshold value, then further operations may depend upon a second threshold value (block  1410 ). The second threshold value may correspond to an upper frequency limit for Clock Generation Circuit  500  to operate in a closed-loop mode, and may, therefore, be set higher than the first threshold value. The frequency of output clock  521  being higher than the second threshold value may indicate that Clock Generation Circuit  500  should operate in open-loop mode to reduce a time to acquire lock by lowering the frequency of output clock  521  more quickly than may be achieved in closed-loop mode. If the frequency of output clock  521  is greater than the second threshold value, then the method moves to block  1414  to adjust the control signal. Otherwise, the method moves to block  1416  to compare phases of divider output signal  522  and ref clock  520 . 
     If the frequency of the clock signal is greater than the second threshold, then the control signal is adjusted based on the measured frequency of the clock signal (block  1414 ). Frequency Monitor  510  asserts FM2 control signal  526 . Similar to FM1 control signal  525  in block  1408 , the assertion of FM2 control signal  526 , causes Clock Generation Circuit  500  to operate in an open-loop mode. As previously disclosed, open-loop mode operation may be enabled in different ways in various embodiments. As an example, in the embodiment of  FIG. 9 , the assertion of FM2 control signal  925  results in Phase Detect  901  and Frequency Divider  909  being disabled. Operation of Charge Pump  903  is determined based on the states of FM1 control signal  925  and FM2 control signal  926 . In the current example, FM2 control signal  926  is asserted, causing Charge Pump  903  to sink current from LPF  905  through CP output signal  927 . LPF  905  discharges, resulting in a reduced voltage level of LPF output signal  928 . The reduced voltage level of LPF output signal  928  at the control input of VCO  907  causes VCO  907  to decrease the frequency of output clock  921 . 
     For another example, in the embodiment of  FIG. 11 , the assertion of FM2 control signal  1125  results in Phase Detect  1101 , Charge Pump  1103 , and Frequency Divider  1109  being disabled. Operation of LPF  1105  is determined based on the states of FM1 control signal  1125  and FM2 control signal  1126 . In this example, FM2 control signal  1126  is asserted, causing LPF  1105  to decrease the voltage level of its output, LPF output signal  1128 . The decreased voltage level of LPF output signal  1128  is received as a control input to VCO  1107 . A decreased voltage level at the control input of VCO  1107  causes VCO  1107  to decrease the frequency of output clock  1121 . In either embodiment, the method may return to block  1404  to continue monitoring the clock signal. 
     If, in block  1410 , it is determined that the frequency of the clock signal is less than the second threshold, then a phase of a divided clock signal is compared to a phase of the reference clock signal (block  1416 ). At this point in the illustrated embodiment, the frequency of output clock  521  has been determined to be between the first and second threshold values. It is noted that the values for the first and second thresholds may be selected based on various parameters of the design of Clock Generation Circuit  500  (or Clock Generation Circuit  900  or Clock Generation Circuit  1100  in various embodiments). For example, the values for the first and second thresholds may be selected to correspond to a target frequency −3% and the target frequency +3%, respectively. The thresholds, in other embodiments, may correspond to any suitable value and may not be symmetric around the target frequency. If necessary, Frequency Monitor  510  de-asserts FM1 control signal  525  or FM2 control signal  526  allowing Clock Generation Circuit  500  to operate in closed-loop mode, including enabling Phase Detect  501  to compare the phase of the divided clock signal (divider output signal  522 ) to the phase of ref clock  520 . 
     The control signal is adjusted dependent upon the result of the phase comparison (block  1418 ). Clock Generation Circuit  500  operates in closed-loop mode while the frequency of output clock  521  is between the first and second threshold values. In closed loop-mode, Phase Detect  501  generates PD up signal  523  and PD down signal  524  dependent upon the relative phases of ref clock  520  and divider output  522 . Charge Pump  503  sources or sinks current at its output dependent on the states of PD up signal  523  and PD down signal  524 , respectively. LPF  505  receives CP output signal  527  and passes low frequency changes in the voltage level (i.e., slow voltage level changes) while filtering high frequency changes in the voltage level. LPF output signal  528  is received by VCO  507 , which adjust the frequency of output clock  521  based on the received LPF output signal  528 . Frequency Divider  509  receives output clock  521  and generates divider output  522  at a frequency that is divided down from the frequency of output clock  521 . 
     It is noted that the method illustrated in  FIG. 14  is merely an example. In other embodiments, variations of this method are contemplated. Some operations may be performed in a different sequence, and/or additional operations may be included. In some embodiments, some operations may occur in parallel. 
     Although specific embodiments have been described above, these embodiments are not intended to limit the scope of the present disclosure, even where only a single embodiment is described with respect to a particular feature. Examples of features provided in the disclosure are intended to be illustrative rather than restrictive unless stated otherwise. The above description is intended to cover such alternatives, modifications, and equivalents as would be apparent to a person skilled in the art having the benefit of this disclosure. 
     The scope of the present disclosure includes any feature or combination of features disclosed herein (either explicitly or implicitly), or any generalization thereof, whether or not it mitigates any or all of the problems addressed herein. Accordingly, new claims may be formulated during prosecution of this application (or an application claiming priority thereto) to any such combination of features. In particular, with reference to the appended claims, features from dependent claims may be combined with those of the independent claims and features from respective independent claims may be combined in any appropriate manner and not merely in the specific combinations enumerated in the appended claims.

Metadata:
Filing Date: 20160810
Publication Date: 20171205
Grant Date: 20171205
Priority Date: 20160810
Inventors: DENG WEI
FISCHETTE, JR. DENNIS
YEE GIN
Assignee: APPLE INC
CPC Classifications: [{"code": "H03L7/0891", "inventive": true, "first": false, "tree": "[]"}, {"code": "H03L7/0891", "inventive": true, "first": true, "tree": "[]"}, {"code": "H03L7/1072", "inventive": true, "first": false, "tree": "[]"}, {"code": "H03L7/1075", "inventive": true, "first": true, "tree": "[]"}, {"code": "H03L7/113", "inventive": true, "first": false, "tree": "[]"}, {"code": "H03L7/18", "inventive": true, "first": false, "tree": "[]"}, {"code": "H03L7/0891", "inventive": true, "first": true, "tree": "[]"}]
Family ID: 60452140