# Using DTMB-Based Passive Radar for Small Unmanned Aerial Vehicle Detection

Authors: Huijie Zhu; Lijun Wang; Mingqian Liu
Journal: Wireless Communications and Mobile Computing
 (2021)

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## Abstract

There is inevitable polarization angle deviation between the target echo signal and the direct path signal of illuminator of opportunity (IO) in passive radar. In order to investigate the potential performance loss in target detection induced by the random deviation, small unmanned aerial vehicle (UAV) detection experiments with digital television terrestrial multimedia broadcasting- (DTMB-) based passive radar are conducted in this paper. Experimental results show that the polarization angles of the clutter signal and target echo signal are inconsistent. When the polarization diversity technology is used to suppress the clutter signal, the processing performance of the target echo signal may be reduced. On the premise that clutter is effectively suppressed by the processing algorithm, polarization synthesis can maximize the target echo signal processing gain. The effectiveness of the target localization algorithm combining time difference of arrival (TDOA) and direction of arrival (DOA) is also verified with polarization diversity reception in this paper.


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## Body

## 1. Introduction

Passive radar is a type of special bistatic or multistatic radar which exploits the existing electromagnetic signals in space as illuminators of opportunity (IOs) and realizes target detection and localization through passive reception. As its features of no dedicated transmitter and no frequency assignment, passive radar has attracted wide attention from academia and industry. FM radio [1, 2], digital TV [3, 4], mobile communications [5, 6], Wi-Fi [7, 8], WiMAX [9–11], satellite communications [12, 13], and many other IOs have been exploited for passive radar, which makes it achieve remarkable development over the years.The IOs are not purposely designed for target detection; as a result, passive radar needs complicated signal processing to ensure its performance. However, the cost of signal processing has been greatly reduced with the development of high-performance computing technology. Furthermore, the development of software-defined radio technology makes passive radar be developed towards software-defined radar. The passive radar researchers only need to focus on algorithms rather than hardware platforms, which greatly promotes the iterative evolution of passive radar processing algorithms. The signal processing of passive radar has approached its ultimate performance at present, and it is urgent to find new ways to improve the performance of passive radar.In recent years, polarization diversity is generally considered a feasible way to further improve the passive radar performance [1, 14–18]. However, most studies focused on realizing clutter suppression by taking advantage of polarization diversity technology. While the clutter signal is effectively suppressed, the detection performance of the target echo signal may be limited by the polarization angle deviation between the clutter signal and the echo signal.In order to verify the performance of the polarization diversity-based echo signal detection, field experiments with dual-polarization reception are carried out in this paper. The digital television terrestrial multimedia broadcasting (DTMB) signal is exploited as the IO signal while the unmanned aerial vehicle (UAV) of DJI Mavic 2 is selected as the target. DTMB is an international terrestrial high-definition television broadcasting standard led by China. The bandwidth of the DTMB signal is about 8 MHz while the transmission power is usually between 300 and 1000 watts.The rest of this paper is organized as follows. Section2 introduces the signal model for passive radar in detail. Section 3 analyzes the polarization diversity for clutter suppression and target detection, together with the polarization-induced problem. Section 4 discusses the experimental process and results. Finally, conclusions and future work are summarized in Section 5.


## 2. Signal Model for Passive Radar

### 2.1. Signal Model for Receiving Channels

A passive radar system generally consists of two synchronous receiving channels, which are called the reference channel and surveillance channel, respectively. The received signalxrt of the reference channel can be described as
(1)xrt=Cr⋅st+∑i=1LCr,i⋅st−τi+wrt,where st is the pure signal transmitted by the IO source, Cr is the amplitude, L is the number of multipath reflection, Cr,i and τi are the amplitude and time delay of the ith multipath, respectively, and wrt is the noise in the reference channel. xrt usually has a high signal-to-noise ratio (SNR) as the reference antenna is in the direction of the IO when the passive radar is in operation. Especially for the digital modulated signal, we can reconstruct the pure signal st from xrt by means of demodulation and remodulation [4]; (1) can then be simply rewritten as
(2)xrt≈Cr⋅st.The received signalxst of the surveillance channel can be written as
(3)xst=∑i=0NcCs,i⋅st−τs,i+∑i=Nc+1Nc+NsCs,i⋅st−τs,i+∑i=1NmCm,i⋅st−τm,iej2πfit+wst;in (3), Cs,i and τs,i are the amplitude and time delay of the ith stationary object echo (including multipath), respectively, and i=0 is for the direct path signal (DPS) received from the side lobe of the surveillance antenna. Cm,i, τm,i, and fi are the amplitude, time delay, and Doppler frequency of the ith moving target echo, respectively. Nc is the number of clutter echoes (excluding the DPS), Ns is the number of stationary targets, Nm is the number of moving targets, and wst is the noise in the surveillance channel.


### 2.2. Signal Model for Clutter Suppression

The energy of the target echo is far weaker than that of clutter in passive radar. Clutter suppression is crucial for the operation of passive radar as it may mask target echoes. The least-squares (LS) matrix solution, sometimes referred to as the extensive cancelation algorithm (ECA) or direct matrix inversion (DMI), is a widely used method as its inherently parallel algorithm structure that can be perfectly accelerated by hardware implementation [19, 20]. According to (3), the signal model for the surveillance channel can be written in a discrete form after sampling as
(4)xsn=xcn+xtn+wsn=∑i=0KcCs,i⋅sn−i+xtn+wsn,where xcn, xtn, and wsn are the discrete form of clutter echoes, target echoes (both stationary and moving), and noise, respectively. sn is the discrete form of st, Kc is the maximum integer number corresponding to a signal delay in samples of the clutter echoes, and (4) can be rewritten in a compact matrix form as
(5)Xs=S⋅Cs+Xt+Ws;in (5),
(6)Xs=xsnxsn+1⋯xsn+NT,(7)S=snsn−1⋯sn−Kcsn+1sn⋯sn−Kc+1⋮⋮⋱⋮sn+Nsn+N−1⋯sn+N−Kc,(8)Cs=Cs,0Cs,1⋯Cs,KcT,(9)Xt=xtnxtn+1⋯xtn+NT,(10)Ws=wsnwsn+1⋯wsn+NT,where N is the number of available samples and ·T indicates matrix transposition.The ECA-based solution is first to solve the following optimization problem:(11)minCJ=Xs−S⋅C2.The solution of (11) can be found by calculating the pseudoinverse of S:
(12)C=SHS−1SHXs,where ·H indicates matrix conjugate transposition. The calculated coefficient vector C represents estimated values of the clutter amplitudes for successive delays of the reference signal. Then, the clutter suppression can be expressed as
(13)Xrem=Xs−S⋅C;in (13),
(14)Xrem=xremnxremn+1⋯xremn+NTis the residual target echo signal vector after clutter cancellation.For the operation of passive radar, a substitution ofxrt for st is usually valid due to the high SNR. As a result, the clutter suppression in practice is performed as
(15)Xrem=Xs−XrXrHXr−1XrHXs;in (15),
(16)Xr=xrnxrn−1⋯xrn−Kcxrn+1xrn⋯xrn−Kc+1⋮⋮⋱⋮xrn+Nxrn+N−1⋯xrn+N−Kc,where xrn is the discrete form of xrt.


### 2.3. Signal Model for Target Detection and Localization

Target detection in passive radar is achieved by applying a cross-ambiguity function (CAF) to the residual target echo and the time-Doppler shifted visions of the reference signal. The calculation process is defined as(17)ψl,k=∑n=0N−1xremnxr∗n−le−j2πnk/N;by maximizing the CAF, the bistatic parameter pair of the strongest target echo signal can be estimated as
(18)lt,kt=argmaxl,kψl,k;then, the estimated time delay τt and Doppler-shift ft can be derived as
(19)τt=ltfs,ft=ktfsN.The time difference of arrival (TDOA) measurement method for finding a target position has been widely used in the presence of multiple transmitters or multiple receivers [21–24]. The main target localization method used for bistatic passive radar is based on the measurements of bistatic range and direction of arrival (DOA) [25–31]. Different from the beamforming-based DOA estimation technique, a 2-D interferometric approach is exploited to estimate the DOA of the target echo in this paper. Though the beamforming technique can enhance the signal-to-disturbance ratio, the interferometric approach is simple and sufficient to verify the superiority of polarization diversity.According to (17) and (18), the CAF results of the M surveillance channels can be described as
(20)ψlt,kt=ψ0lt,ktψ1lt,kt⋯ψM−1lt,ktT=ad,α∑n=0N−1xremnxr∗n−lte−j2πnkt/N,where ad,α=a0d0,α,a1d1,α,⋯,aM−1dM−1,αT is the steering vector of the antenna array, dmm=0,1,⋯,M−1 is the distance difference between the mth and the reference antenna elements, and α is the DOA of the target echo. Therefore, DOA estimation based on the CAF results is completely equivalent to the interferometer direction finding.Figure1 shows the bistatic plane within a 2-D coordinate system, where the coordinates of receiver, transmitter, and target are xR,yR,xT,yT,andxi,yi, respectively. Without loss of generality, we can set xR,yR as 0,0 for simplification. Then, the baseline L can be calculated from the known positions of both receiver and transmitter as
(21)L=xT2+yT2;the range between the transmitter and the target RT can be derived from the unknown position of the target and the known transmitter as
(22)RT=xT−xi2+yT−yi2;similarly, RR shown in Figure 1 can be described as
(23)RR=xi2+yi2;with the estimations of time delay τt and target echo DOA α, additional equations can be obtained as
(24)c⋅τt=RT+RR−L,tanα=yixi,where c is the speed of propagation.Figure 1
Bistatic plane within a 2-D coordinate system.The closed-form localization result can be realized by solving (22), (23), and (24) as
(25)xi=c⋅τt⋅2L+c⋅τtcosα2L+c⋅τt−2xT−2yTsinα,yi=c⋅τt⋅2L+c⋅τtsinα2L+c⋅τt−2xT−2yTsinα.


## 2.1. Signal Model for Receiving Channels

A passive radar system generally consists of two synchronous receiving channels, which are called the reference channel and surveillance channel, respectively. The received signalxrt of the reference channel can be described as
(1)xrt=Cr⋅st+∑i=1LCr,i⋅st−τi+wrt,where st is the pure signal transmitted by the IO source, Cr is the amplitude, L is the number of multipath reflection, Cr,i and τi are the amplitude and time delay of the ith multipath, respectively, and wrt is the noise in the reference channel. xrt usually has a high signal-to-noise ratio (SNR) as the reference antenna is in the direction of the IO when the passive radar is in operation. Especially for the digital modulated signal, we can reconstruct the pure signal st from xrt by means of demodulation and remodulation [4]; (1) can then be simply rewritten as
(2)xrt≈Cr⋅st.The received signalxst of the surveillance channel can be written as
(3)xst=∑i=0NcCs,i⋅st−τs,i+∑i=Nc+1Nc+NsCs,i⋅st−τs,i+∑i=1NmCm,i⋅st−τm,iej2πfit+wst;in (3), Cs,i and τs,i are the amplitude and time delay of the ith stationary object echo (including multipath), respectively, and i=0 is for the direct path signal (DPS) received from the side lobe of the surveillance antenna. Cm,i, τm,i, and fi are the amplitude, time delay, and Doppler frequency of the ith moving target echo, respectively. Nc is the number of clutter echoes (excluding the DPS), Ns is the number of stationary targets, Nm is the number of moving targets, and wst is the noise in the surveillance channel.


## 2.2. Signal Model for Clutter Suppression

The energy of the target echo is far weaker than that of clutter in passive radar. Clutter suppression is crucial for the operation of passive radar as it may mask target echoes. The least-squares (LS) matrix solution, sometimes referred to as the extensive cancelation algorithm (ECA) or direct matrix inversion (DMI), is a widely used method as its inherently parallel algorithm structure that can be perfectly accelerated by hardware implementation [19, 20]. According to (3), the signal model for the surveillance channel can be written in a discrete form after sampling as
(4)xsn=xcn+xtn+wsn=∑i=0KcCs,i⋅sn−i+xtn+wsn,where xcn, xtn, and wsn are the discrete form of clutter echoes, target echoes (both stationary and moving), and noise, respectively. sn is the discrete form of st, Kc is the maximum integer number corresponding to a signal delay in samples of the clutter echoes, and (4) can be rewritten in a compact matrix form as
(5)Xs=S⋅Cs+Xt+Ws;in (5),
(6)Xs=xsnxsn+1⋯xsn+NT,(7)S=snsn−1⋯sn−Kcsn+1sn⋯sn−Kc+1⋮⋮⋱⋮sn+Nsn+N−1⋯sn+N−Kc,(8)Cs=Cs,0Cs,1⋯Cs,KcT,(9)Xt=xtnxtn+1⋯xtn+NT,(10)Ws=wsnwsn+1⋯wsn+NT,where N is the number of available samples and ·T indicates matrix transposition.The ECA-based solution is first to solve the following optimization problem:(11)minCJ=Xs−S⋅C2.The solution of (11) can be found by calculating the pseudoinverse of S:
(12)C=SHS−1SHXs,where ·H indicates matrix conjugate transposition. The calculated coefficient vector C represents estimated values of the clutter amplitudes for successive delays of the reference signal. Then, the clutter suppression can be expressed as
(13)Xrem=Xs−S⋅C;in (13),
(14)Xrem=xremnxremn+1⋯xremn+NTis the residual target echo signal vector after clutter cancellation.For the operation of passive radar, a substitution ofxrt for st is usually valid due to the high SNR. As a result, the clutter suppression in practice is performed as
(15)Xrem=Xs−XrXrHXr−1XrHXs;in (15),
(16)Xr=xrnxrn−1⋯xrn−Kcxrn+1xrn⋯xrn−Kc+1⋮⋮⋱⋮xrn+Nxrn+N−1⋯xrn+N−Kc,where xrn is the discrete form of xrt.


## 2.3. Signal Model for Target Detection and Localization

Target detection in passive radar is achieved by applying a cross-ambiguity function (CAF) to the residual target echo and the time-Doppler shifted visions of the reference signal. The calculation process is defined as(17)ψl,k=∑n=0N−1xremnxr∗n−le−j2πnk/N;by maximizing the CAF, the bistatic parameter pair of the strongest target echo signal can be estimated as
(18)lt,kt=argmaxl,kψl,k;then, the estimated time delay τt and Doppler-shift ft can be derived as
(19)τt=ltfs,ft=ktfsN.The time difference of arrival (TDOA) measurement method for finding a target position has been widely used in the presence of multiple transmitters or multiple receivers [21–24]. The main target localization method used for bistatic passive radar is based on the measurements of bistatic range and direction of arrival (DOA) [25–31]. Different from the beamforming-based DOA estimation technique, a 2-D interferometric approach is exploited to estimate the DOA of the target echo in this paper. Though the beamforming technique can enhance the signal-to-disturbance ratio, the interferometric approach is simple and sufficient to verify the superiority of polarization diversity.According to (17) and (18), the CAF results of the M surveillance channels can be described as
(20)ψlt,kt=ψ0lt,ktψ1lt,kt⋯ψM−1lt,ktT=ad,α∑n=0N−1xremnxr∗n−lte−j2πnkt/N,where ad,α=a0d0,α,a1d1,α,⋯,aM−1dM−1,αT is the steering vector of the antenna array, dmm=0,1,⋯,M−1 is the distance difference between the mth and the reference antenna elements, and α is the DOA of the target echo. Therefore, DOA estimation based on the CAF results is completely equivalent to the interferometer direction finding.Figure1 shows the bistatic plane within a 2-D coordinate system, where the coordinates of receiver, transmitter, and target are xR,yR,xT,yT,andxi,yi, respectively. Without loss of generality, we can set xR,yR as 0,0 for simplification. Then, the baseline L can be calculated from the known positions of both receiver and transmitter as
(21)L=xT2+yT2;the range between the transmitter and the target RT can be derived from the unknown position of the target and the known transmitter as
(22)RT=xT−xi2+yT−yi2;similarly, RR shown in Figure 1 can be described as
(23)RR=xi2+yi2;with the estimations of time delay τt and target echo DOA α, additional equations can be obtained as
(24)c⋅τt=RT+RR−L,tanα=yixi,where c is the speed of propagation.Figure 1
Bistatic plane within a 2-D coordinate system.The closed-form localization result can be realized by solving (22), (23), and (24) as
(25)xi=c⋅τt⋅2L+c⋅τtcosα2L+c⋅τt−2xT−2yTsinα,yi=c⋅τt⋅2L+c⋅τtsinα2L+c⋅τt−2xT−2yTsinα.


## 3. Polarization Diversity and Problem Analysis

There is inevitable polarization angle deviation between the echo signal and the incident signal. The effects of polarization have not been taken into account in the signal model above. When the polarization angle is present, (3) can be rewritten as
(26)xst=∑i=0NcCs,i⋅st−τs,i⋅cosθs,i+∑i=Nc+1Nc+NsCs,i⋅st−τs,i⋅cosθs,i+∑i=1NmCm,i⋅st−τm,iej2πfit⋅cosθm,i+wst,where θs,i and θm,i are the polarization angles of the ith stationary object echo and the ith moving object echo, respectively, and they are parameters that we can control under polarization diversity reception.Most of the IOs for passive radar are transmitted by horizontal or vertical polarization antennas. Assume we use an orthogonal dual-polarized antenna as the surveillance antenna, the received signal vector can be described as(27)Xn=x0∘nx90∘n=cosθsinθ⋅ejφxsn,where x0°n is one output of the dual-polarized antenna and x90°n is the other, θ is the polarization angle determined by the antenna, and φ is the phase difference between the two orthogonal channels. After polarization diversity reception, the arbitrary polarization angle can be realized by polarization synthesis as follows:
(28)x^sn,ϑ,ϕ=cosϑsinϑ⋅ejϕ∗x0∘nx90∘n=cosϑsinϑ⋅e−jϕcosθsinθ⋅ejφxsn=cosϑcosθ+sinϑsinθ⋅ejφ−ϕ⋅xsn;in (28), ·∗ indicates the conjugate operation. By substituting ϕ=φ in (28), we obtain
(29)x^sn,ϑ=cosθ−ϑ⋅xsn,which means that the polarization angle has changed. We can then rewrite (15) as
(30)Xremϑ,ϕ=X^s−XrXrHXr−1XrHX^s.The essence of clutter suppression by taking advantage of polarization diversity technology can be expressed as(31)minϑ,ϕJ=Xremϑ,ϕ2;the optimal polarization synthesis parameter pair for clutter suppression can be described as
(32)θc,φc=argminϑ,ϕXremϑ,ϕ2.On the premise that clutter can be effectively suppressed by a processing algorithm, target detection in passive radar will only depend on the CAF operation. The optimal polarization synthesis parameter pair for thelt,kt target detection can be obtained as
(33)θt,φt=argmaxϑ,ϕψ^lt,kt,ϑ,ϕ=argmaxϑ,ϕ∑n=0N−1xremn,ϑ,ϕxr∗n−lte−j2πnkt/N,where xremn,ϑ,ϕ is the element of Xremϑ,ϕ.Therefore, when the parameter pairs ofθc,φc and θt,φt are inconsistent, clutter suppression based on the polarization diversity technology will result in performance loss for the target detection.


## 4. Experimental Analysis

In order to verify the theoretical analysis above, we conduct an experimental system which consists of a reference antenna, surveillance antenna, software-defined radio (SDR) receiver, and heterogeneous computing platform. The experimental antenna system is shown in Figure2. It is mainly composed of a vertical polarization antenna and a dual-polarized antenna.Figure 2
The experimental antenna system.


### 4.1. Reference Signal Reconstruction

It can be clearly seen from Figure2 that the DTMB transmitting antenna is visible to the reference antenna. Therefore, the reference signal has a high SNR. Further, reference signal reconstruction is adopted to remove the inevitable multipath and noise. The channel decoding and coding operations are omitted in our processing due to the high SNR, and the whole reference signal reconstruction process is given in Figure 3.Figure 3
Reference signal reconstruction process.Matched filtering is first performed to reduce intersymbol interference for the received signal. Then, synchronization, channel estimation and equalization, OFDM demodulation, and other operations are carried out in turn.A multichannel synchronous SDR receiver is used for signal acquisition, which can turn the radio frequency and sampling rate flexibly. The carrier frequency of the DTMB signal exploited in our experiments is 754 MHz, and the used sampling rate is 30.24 MHz, which means that the oversampling rate is 4. The duration of the reference signal used for demodulation is 0.1 s. Figure4 shows the obtained one-frame constellation after OFDM demodulation. According to the DTMB standard, the frame body of the DTMB signal consists of two different types of symbols, the system information (SI) symbol and the streaming data symbol. The SI symbol is mapped to the BPSK constellation fixedly while the streaming data symbol can be mapped to one of the 4QAM, 16QAM, 32QAM, and 64QAM constellations. Both the BPSK and 16QAM constellations can be seen in Figure 4, in which all the constellation points are focused.Figure 4
The constellation of reference signal after demodulation (one frame).After constellation demapping and deinterleave, we make a hard decision to recover the transmitted bit sequence. Finally, the recovered bit sequence is processed by the operations of interleave, constellation mapping, OFDM modulation, framing, and shaping filtering, which are the same as the transmitter, to reconstruct the pure reference signal.


### 4.2. Target Detection

The DJI Mavic 2 UAV, which has unfold dimensions of322mm×242mm×84mm is used as the target to be detected in our experiments. The clutter suppression is first conducted by using the ECA-based solution with the reconstructed reference signal and one of the dual-polarized echo signals, and the result is given in Figure 5. It shows that a suppression capacity of about 30 dB is achieved. Since the reconstructed reference signal cannot be consistent with the clutter components in terms of frequency deviation and time delay variation, the residual signal still has some noise components.Figure 5
PSD comparison: before and after clutter suppression.The decimation filter and fast Fourier transform (FFT) are used after clutter suppression to realize the CAF operation as (17). The detailed schematic is shown in Figure 6.Figure 6
CAF processing schematic.The obtained bistatic Rang-Doppler (RD) map after the CAF processing is shown in Figure7. As can be seen, there is an obvious target that the bistatic range equals 119.05 m and the bistatic Doppler frequency equals 35 Hz.Figure 7
RD map after CAF processing.


### 4.3. Polarization Diversity for Clutter Suppression

In the clutter signal, the polarization angle of the DPS component is different from that of the multipath components. Therefore, we cannot suppress every component by the way of polarization diversity.We evaluate the power of the polarization synthesized signal as (28). When −180°≤θ≤180° and −180°≤φ≤180°, the obtained signal power is shown in Figure 8. For different polarization parameter pairs, the power of the synthesized signal can differ by larger than 10.5 dB.Figure 8
Normalized power (dB) of the polarization synthesized signal for−180°≤θ≤180° and −180°≤φ≤180°.There are four maximums and four minimums in the range of [-180°, 180°] due to the symmetry of trigonometric functions. Then, we narrow the range to [-90°, 90°] and obtain the partial but complete results shown in Figure9. In this range, the synthesized signal gets its maximum value with the parameter pair θ,φ at 28°,−32° while its minimum value is at −62°,−32°. As a result, the value of -32° is the estimation of the phase difference between the two orthogonal channels, and the estimated value of 28° is treated as the equivalent polarization angle of the composite clutter signal. The optimal polarization angle used for clutter suppression has a value of -62° in our experiments.Figure 9
Normalized power (dB) of the polarization synthesized signal for−90≤θ≤90° and −90°≤φ≤90°.


### 4.4. Polarization Diversity for Target Detection

The target detection performance under different polarization angles is also evaluated in our experiments. Since different polarization angles may result in different residual noise components by the ECA-based solution, the SNR of the RD map defined is used in the evaluation:(34)SNRt=ψτt,ftmeanτ,fψτ,f.The obtained normalizedSNRt map is shown in Figure 10.Figure 10
NormalizedSNRt (dB) map for −90°≤θ≤90° and −90°≤φ≤90°.It shows thatSNRt gets its maximum value with the parameter pair θ,φ at (-49°, -32°) while its minimum value at (41°, -32°), and the difference between the maximum and minimum is larger than 11.5 dB. As the phase difference between the two orthogonal channels is only related to the receiver, it can be seen that the value of φ for the extremum in Figure 10 is the same as that in Figure 9. However, the polarization angle of -49° for the maximum of SNRt is inconsistent with the optimal value of -62° for clutter suppression. As a result, it proves that clutter suppression based on the polarization diversity technology may result in performance loss for the target detection due to the randomness of the polarization angle difference.Table1 shows the obtained normalized SNRt with several polarization angles we are interested in. We only use one of the dual-polarization echo signals in the case of θ=0°. As the noises in the two orthogonal polarized channels are not correlated with each other, the random noise components will be superimposed after polarization synthesis. In addition to the random noise, the clutter signal and target echo signal in the synthesized signal are affected dramatically by changing the polarization angle parameter. Only when the polarization angle adopted in the polarization synthesis matches the actual signal polarization angle, the SNR of the synthesized signal can be maximized. Table 1 shows that polarization matching has a performance improvement of about 1.22 dB compared with single-polarization reception in our experiments.Table 1
Comparison ofSNRt.
θφNormalizedSNRt (dB)0°0°-1.2228728°-32°-3.19481-62°-32°-0.58790-49°-32°0As the stability of the ECA-based clutter suppression algorithm is related to the calculating precision of matrix operation, the effect of clutter suppression will not change with the amplitude of the clutter signal in a certain range. The algorithm always works within the stable range in our experiments, and the clutter signal can be well suppressed at all the polarization angles. Although there is a performance improvement of up to 2.61 dB compared to 28° at -62°, we need to point out that this is not the reason for better clutter suppression; the theoretical reason is that this polarization angle is closer to the actual polarization angle of -49°. When the clutter signal is too strong for the ECA algorithm to work normally, polarization diversity is an effective way to increase the additional capacity for clutter suppression. Though there may be performance loss for target detection, it is worthful for the normal operation of the system.


### 4.5. Target Localization

A small antenna array which consists of three elements is exploited to estimate the DOA of the UAV echo. Figure11 shows the configuration of the antenna array, which consists of three antenna elements. Each antenna element is orthogonally dual-polarized as shown in the figure, where H represents horizontal polarization and V represents vertical polarization. The spacing is 28 cm for Element 0 and Element 1, while it is 42 cm for Element 1 and Element 2. Since a virtual spacing of 14 cm can be constructed by this nonuniform linear array, which is below the half-wavelength of about 20 cm in our experiments, it will not lead to the cyclically ambiguous problem in DOA estimation. For each dual-polarized element, we conduct polarization synthesis, clutter suppression, and TDOA estimation separately. The three processing results are further used for DOA estimation. The positioning result of the target is finally obtained after both TDOA and DOA estimations.Figure 11
Array configuration of the 2-D interferometer.The essence of the 2-D interferometer direction finding is to determine the direction of the signal source by the phase difference formed by the received signal on different antenna elements. The wave-path difference between the two antenna elements will cause the phase difference. Though the polarization angle is random, it is not instantaneous. As a result, we use the same value for the parameter ofθ in polarization synthesis of all the three dual-polarized antenna elements. Since the parameter of φ is mainly related to different channels of the receiver, we use the premeasured values for it. We search optimal DOA estimation between -90° and 90°. The result of the direction finding at a certain moment is shown in Figure 12, which shows an optimal estimation of about 20°.Figure 12
DOA output of the 2-D interferometer.The combination of TDOA and DOA as (25) is adopted to locate the UAV. Figure 13 shows the positioning result of the UAV in a certain continuous time, which is consistent with its actual flight path in the experiments. The two obvious discontinuous sudden changes in Figure 13 are caused by the range resolution of the signal, which is about 39.68 m.Figure 13
Positioning result of the UAV with the combination of TDOA and DOA.Figure13 shows that the direction finding and localization of the echo signal can still be realized after polarization synthesis, which verifies the validity of the localization algorithm in passive radar with polarization diversity reception. The positioning distance may increase significantly at some polarization angles through polarization synthesis. However, since there is only 1.22 dB performance improvement in target detection compared with single-polarization reception in our experiments, the positioning distance will not increase obviously.


## 4.1. Reference Signal Reconstruction

It can be clearly seen from Figure2 that the DTMB transmitting antenna is visible to the reference antenna. Therefore, the reference signal has a high SNR. Further, reference signal reconstruction is adopted to remove the inevitable multipath and noise. The channel decoding and coding operations are omitted in our processing due to the high SNR, and the whole reference signal reconstruction process is given in Figure 3.Figure 3
Reference signal reconstruction process.Matched filtering is first performed to reduce intersymbol interference for the received signal. Then, synchronization, channel estimation and equalization, OFDM demodulation, and other operations are carried out in turn.A multichannel synchronous SDR receiver is used for signal acquisition, which can turn the radio frequency and sampling rate flexibly. The carrier frequency of the DTMB signal exploited in our experiments is 754 MHz, and the used sampling rate is 30.24 MHz, which means that the oversampling rate is 4. The duration of the reference signal used for demodulation is 0.1 s. Figure4 shows the obtained one-frame constellation after OFDM demodulation. According to the DTMB standard, the frame body of the DTMB signal consists of two different types of symbols, the system information (SI) symbol and the streaming data symbol. The SI symbol is mapped to the BPSK constellation fixedly while the streaming data symbol can be mapped to one of the 4QAM, 16QAM, 32QAM, and 64QAM constellations. Both the BPSK and 16QAM constellations can be seen in Figure 4, in which all the constellation points are focused.Figure 4
The constellation of reference signal after demodulation (one frame).After constellation demapping and deinterleave, we make a hard decision to recover the transmitted bit sequence. Finally, the recovered bit sequence is processed by the operations of interleave, constellation mapping, OFDM modulation, framing, and shaping filtering, which are the same as the transmitter, to reconstruct the pure reference signal.


## 4.2. Target Detection

The DJI Mavic 2 UAV, which has unfold dimensions of322mm×242mm×84mm is used as the target to be detected in our experiments. The clutter suppression is first conducted by using the ECA-based solution with the reconstructed reference signal and one of the dual-polarized echo signals, and the result is given in Figure 5. It shows that a suppression capacity of about 30 dB is achieved. Since the reconstructed reference signal cannot be consistent with the clutter components in terms of frequency deviation and time delay variation, the residual signal still has some noise components.Figure 5
PSD comparison: before and after clutter suppression.The decimation filter and fast Fourier transform (FFT) are used after clutter suppression to realize the CAF operation as (17). The detailed schematic is shown in Figure 6.Figure 6
CAF processing schematic.The obtained bistatic Rang-Doppler (RD) map after the CAF processing is shown in Figure7. As can be seen, there is an obvious target that the bistatic range equals 119.05 m and the bistatic Doppler frequency equals 35 Hz.Figure 7
RD map after CAF processing.


## 4.3. Polarization Diversity for Clutter Suppression

In the clutter signal, the polarization angle of the DPS component is different from that of the multipath components. Therefore, we cannot suppress every component by the way of polarization diversity.We evaluate the power of the polarization synthesized signal as (28). When −180°≤θ≤180° and −180°≤φ≤180°, the obtained signal power is shown in Figure 8. For different polarization parameter pairs, the power of the synthesized signal can differ by larger than 10.5 dB.Figure 8
Normalized power (dB) of the polarization synthesized signal for−180°≤θ≤180° and −180°≤φ≤180°.There are four maximums and four minimums in the range of [-180°, 180°] due to the symmetry of trigonometric functions. Then, we narrow the range to [-90°, 90°] and obtain the partial but complete results shown in Figure9. In this range, the synthesized signal gets its maximum value with the parameter pair θ,φ at 28°,−32° while its minimum value is at −62°,−32°. As a result, the value of -32° is the estimation of the phase difference between the two orthogonal channels, and the estimated value of 28° is treated as the equivalent polarization angle of the composite clutter signal. The optimal polarization angle used for clutter suppression has a value of -62° in our experiments.Figure 9
Normalized power (dB) of the polarization synthesized signal for−90≤θ≤90° and −90°≤φ≤90°.


## 4.4. Polarization Diversity for Target Detection

The target detection performance under different polarization angles is also evaluated in our experiments. Since different polarization angles may result in different residual noise components by the ECA-based solution, the SNR of the RD map defined is used in the evaluation:(34)SNRt=ψτt,ftmeanτ,fψτ,f.The obtained normalizedSNRt map is shown in Figure 10.Figure 10
NormalizedSNRt (dB) map for −90°≤θ≤90° and −90°≤φ≤90°.It shows thatSNRt gets its maximum value with the parameter pair θ,φ at (-49°, -32°) while its minimum value at (41°, -32°), and the difference between the maximum and minimum is larger than 11.5 dB. As the phase difference between the two orthogonal channels is only related to the receiver, it can be seen that the value of φ for the extremum in Figure 10 is the same as that in Figure 9. However, the polarization angle of -49° for the maximum of SNRt is inconsistent with the optimal value of -62° for clutter suppression. As a result, it proves that clutter suppression based on the polarization diversity technology may result in performance loss for the target detection due to the randomness of the polarization angle difference.Table1 shows the obtained normalized SNRt with several polarization angles we are interested in. We only use one of the dual-polarization echo signals in the case of θ=0°. As the noises in the two orthogonal polarized channels are not correlated with each other, the random noise components will be superimposed after polarization synthesis. In addition to the random noise, the clutter signal and target echo signal in the synthesized signal are affected dramatically by changing the polarization angle parameter. Only when the polarization angle adopted in the polarization synthesis matches the actual signal polarization angle, the SNR of the synthesized signal can be maximized. Table 1 shows that polarization matching has a performance improvement of about 1.22 dB compared with single-polarization reception in our experiments.Table 1
Comparison ofSNRt.
θφNormalizedSNRt (dB)0°0°-1.2228728°-32°-3.19481-62°-32°-0.58790-49°-32°0As the stability of the ECA-based clutter suppression algorithm is related to the calculating precision of matrix operation, the effect of clutter suppression will not change with the amplitude of the clutter signal in a certain range. The algorithm always works within the stable range in our experiments, and the clutter signal can be well suppressed at all the polarization angles. Although there is a performance improvement of up to 2.61 dB compared to 28° at -62°, we need to point out that this is not the reason for better clutter suppression; the theoretical reason is that this polarization angle is closer to the actual polarization angle of -49°. When the clutter signal is too strong for the ECA algorithm to work normally, polarization diversity is an effective way to increase the additional capacity for clutter suppression. Though there may be performance loss for target detection, it is worthful for the normal operation of the system.


## 4.5. Target Localization

A small antenna array which consists of three elements is exploited to estimate the DOA of the UAV echo. Figure11 shows the configuration of the antenna array, which consists of three antenna elements. Each antenna element is orthogonally dual-polarized as shown in the figure, where H represents horizontal polarization and V represents vertical polarization. The spacing is 28 cm for Element 0 and Element 1, while it is 42 cm for Element 1 and Element 2. Since a virtual spacing of 14 cm can be constructed by this nonuniform linear array, which is below the half-wavelength of about 20 cm in our experiments, it will not lead to the cyclically ambiguous problem in DOA estimation. For each dual-polarized element, we conduct polarization synthesis, clutter suppression, and TDOA estimation separately. The three processing results are further used for DOA estimation. The positioning result of the target is finally obtained after both TDOA and DOA estimations.Figure 11
Array configuration of the 2-D interferometer.The essence of the 2-D interferometer direction finding is to determine the direction of the signal source by the phase difference formed by the received signal on different antenna elements. The wave-path difference between the two antenna elements will cause the phase difference. Though the polarization angle is random, it is not instantaneous. As a result, we use the same value for the parameter ofθ in polarization synthesis of all the three dual-polarized antenna elements. Since the parameter of φ is mainly related to different channels of the receiver, we use the premeasured values for it. We search optimal DOA estimation between -90° and 90°. The result of the direction finding at a certain moment is shown in Figure 12, which shows an optimal estimation of about 20°.Figure 12
DOA output of the 2-D interferometer.The combination of TDOA and DOA as (25) is adopted to locate the UAV. Figure 13 shows the positioning result of the UAV in a certain continuous time, which is consistent with its actual flight path in the experiments. The two obvious discontinuous sudden changes in Figure 13 are caused by the range resolution of the signal, which is about 39.68 m.Figure 13
Positioning result of the UAV with the combination of TDOA and DOA.Figure13 shows that the direction finding and localization of the echo signal can still be realized after polarization synthesis, which verifies the validity of the localization algorithm in passive radar with polarization diversity reception. The positioning distance may increase significantly at some polarization angles through polarization synthesis. However, since there is only 1.22 dB performance improvement in target detection compared with single-polarization reception in our experiments, the positioning distance will not increase obviously.


## 5. Conclusion

We have established an experimental system to evaluate the adverse effect of polarization angle on passive radar. By analyzing the experimental data, the necessity of polarization diversity to ensure the target detection performance is revealed. The effect of polarization diversity on clutter suppression is significant; especially when the clutter signal is strong, it is necessary to increase the additional suppression capacity through polarization diversity for the normal operation of the system. However, when the clutter suppression algorithm is sufficient to suppress the clutter, the significance of the polarization diversity will lie in matching the polarization angle of the target echo signal. When the two perfectly match, the maximum SNR of the target echo signal will be achieved, and the system will have the optimal target detection performance. The target localization capacity under polarization synthesis for multichannel is also investigated. We will further study the adaptive polarization synthesis strategy to achieve a compromise between clutter suppression and target detection.



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*Source: 9987992-2021-05-06.xml*