# A Series-Fed Linear Substrate-Integrated Dielectric Resonator Antenna Array for Millimeter-Wave Applications

Authors: Ke Gong; Xue Hui Hu; Peng Hu; Bing Jie Deng; You Chao Tu
Journal: International Journal of Antennas and Propagation
 (2018)

---

## Abstract

A series-fed linear substrate-integrated dielectric resonator antenna array (SIDRAA) is presented for millimeter-wave applications, in which the substrate-integrated dielectric resonator antenna (SIDRA) elements and the feeding structure can be codesigned and fabricated using the same planar process. A prototype 4 × 1 SIDRAA is designed atKa-band and fabricated with a two-layer printed circuit board (PCB) technology. Four SIDRAs are implemented in the Rogers RT6010 substrate using the perforation technique and fed by a compact substrate-integrated waveguide (SIW) through four longitudinal coupling slots within the Rogers RT5880 substrate. The return loss, radiation patterns, and antenna gain were experimentally studied, and good agreement between the measured and simulated results is observed. The SIDRAA example provides a bandwidth of about 10% around 34.5 GHz for 10 dB return loss and stable broadside radiation patterns with the peak gain of 10.5–11.5 dBi across the band.


---

## Body

## 1. Introduction

Dielectric resonator antennas (DRAs) have received widespread attention because of a number of advantages such as small size, high radiation efficiency, wider impedance bandwidth, low conductor loss, no excitation of surface waves, easy of excitation, and so on [1, 2]. These advantages make DRAs excellent candidates for wireless communication systems, especially the ones operated in the millimeter-wave band [3]. Compared with the traditional microstrip antenna and other planar metallic antennas, DRAs also possess higher radiation efficiency for high-frequency applications. However, DRAs are commonly low-gain antennas with a broad radiation pattern for the practical application, and various methods for gain enhancement of single-element DRAs have been reported in the literature [4, 5].Recently, more effort has been devoted to DRA array design to increase the antenna gain for various microwave/millimeter-wave systems [6–17]. Linear rectangular DRA arrays fed by the dielectric image guide (DIG) were investigated at X-band [6, 7], and a DIG-fed double-sided DRA array was proposed at Ka-band with a peak gain of 15.8 dBi [8]. By adding the reflector plane, the eight-element linear DRA array achieved the highest 15.7 dBi gain for microwave application [9]. A significant increase in gain was obtained in [10] by using close interelement spacing for parasitic DRA elements. A compact wideband 2 × 2 DRA array was designed in [11] with the peak gain of 10.5 dBi for microwave imaging systems. A 2 × 2 cylindrical DRA array offered a maximum gain of 14.8 dBi utilizing a nonresonant microstrip patch technique at X-band [12]. Substrate-integrated waveguide- (SIW-) parallel-fed rectangular 1 × 8 and series-fed 4 × 1 DRA arrays were studied and presented together with its circuit model at Ka-band [13, 14]. An SIW-integrated two-dimensional 8 × 8 DRA array was designed in [15] with the measured gain of 21.6 dBi over the operating frequency band 35–37 GHz. A 180-element linear polarized DRA array fed by radial-line waveguide was reported [16] and achieves a maximum gain of 26.7 dBi from 11.96 to 12.08 GHz. Circularly polarized 2 × 2 wideband DRA array and low-sidelobe-level 1 × 6 DRA array achieved a peak gain of 12.17 dBi and 13.43 dBi at C-band, respectively [17]. However, for the abovementioned arrays in [6–17], the DRA elements are usually fabricated singly and assembled one by one, which means higher cost and larger mounting errors, especially for the large-scale arrays in millimeter-wave band. In order to improve the accuracy of the DRA array productions, a novel cofabricated approach for millimeter-wave DRA array designs was demonstrated using the multilayer printed circuit board (PCB) technology [18]. However, the separated DRA elements are fabricated by removing the surrounding dielectric materials, and the feeding network is relatively complex. In our previous work, a substrate-integrated dielectric resonator antenna (SIDRA) was demonstrated with PCB process [19]. However, the SIDRA in [19] is not suitable for compact array application because the transverse coupling slot requires the spacing between two adjacent SIDRA elements to be λg (λg is the guided wavelength in feeding SIW) for cophase exciting.Moreover, different feeding techniques have been used to feed an array of DRAs, such as the dielectric image guide feed [6–8], the microstrip line feed [9–12, 17], the radial-line waveguide feed [16], and the SIW feed [13–15, 18]. Although the microstrip line feeding network is the most frequently employed, its power loss dominates as the operating frequency increases. In contrast, the SIW is a high Q-structure since it is a good compromise between an air-filled rectangular waveguide and a microstrip line [20]. Accordingly, it can minimize the radiation loss and parasitic radiation and provides a low-cost, compact, and low-profile feeding network.In this article, a series-fed linear substrate-integrated dielectric resonator antenna array (SIDRAA) is designed for millimeter-wave applications, in which four SIDRA elements are implemented in the substrate using the perforation technique and fed by a compact SIW feeding network through four longitudinal coupling slots with a distance ofλg/2, and the SIDRA elements along with the feeding structure can be codesigned and fabricated conveniently using the standard PCB process. The proposed SIDRAA has the advantages of low cost, low profile, easy manufacture, compact size, and convenient integration with other planar circuits. In the design, both the SIDRA element and the SIDRAA are simulated and optimized by using Ansoft High Frequency Structure Simulator (HFSS).


## 2. Design of the Antenna Element

### 2.1. Antenna Configuration

Figure1 shows the geometry and parameters of the SIDRA element, including the 3D and top views. The antenna element is mainly composed of two parts: an SIDR and a feeding SIW. The SIDR is integrated in the top Rogers RT6010 (εr1 = 10.2, tanδ = 0.0031 at 10 GHz, thickness h1 = 0.635 mm) substrate using the perforation technique with S1 ≥ λ0/10 and S2 ≥ λ0/10 (λ0 is the wavelength at center frequency in free space) [19]. The end-shorted feeding SIW is constructed in the bottom Rogers RT5880 substrate (εr2 = 2.2, tanδ = 0.0013 at 10 GHz, thickness h2 = 0.254 mm) supporting the dominant mode of TE10 within the antenna operating bandwidth. A longitudinal slot with length of Ls and width of Ws is etched on the SIW broad wall in order to couple the energy to the SIDR element. The distance d1 from the center of slot to the SIW short-circuited end is initially chosen to be λg/4 (λg is the guided wavelength) for the maximum coupling [13], and d2 is the slot offset from the centerline of SIW for good matching. The center of the SIDR is the same as the center of the coupling slot, and the SIDRA element operates at the dominant TE111x mode for radiation. The dielectric waveguide model [2, 21] has been employed to evaluate the dimensions of the SIDRA element with the dominant mode for the resonant frequency f0 of 34.5 GHz as
(1)f0=c2πεr1kx2+ky2+kz2,kx=πa,kz=π2h1,kytankyb2=εr1−1k02−ky2,kx2+ky2+kz2=εr1k02,where εr1 is the relative permittivity of the SIDRA, c is the speed of light, h1 is the thickness of the Rogers RT6010 substrate, k0 is the wavenumber in free space, and kx, ky, and kz indicate the wavenumbers along x, y, and z-directions, respectively. Alternatively, the above equations may be used to determine the dimensions of the SIDR for a desired operation frequency. For example, the resonant frequency of f0 = 34.5 GHz corresponds to an SIDR with dimensions a = b = 3.45 mm and h1 = 0.635 mm. The other geometric parameters of the SIDR and the feeding SIW (including Wsiw, D1, P1, Wt, Lt, Wm, D2, S1, and S2) can be obtained from the method of references [19, 20]. Then, these parameters along with Ls and Ws are optimized by using HFSS for good matching and high radiation performance.Figure 1
Structure of the SIDRA element with the longitudinal coupling slot. (a) 3D view and (b) top view. (Ls = 1.6, Ws = 0.2, d1 = 2.15, d2 = 0.55, all in mm).
(a)
(b)


### 2.2. Simulated Results

Figure2 shows the simulated return loss of the SIDRA element. It can be seen that the element exhibits a 10 dB bandwidth of around 10%. The simulated radiation patterns of the SIDRA at 34.5 GHz are presented in Figure 3, and it can be seen that the 3 dB beamwidths in the E(yz)- and H(xz)-planes are about 140° and 70°, respectively. The simulated gain of the element is 4.9–5.6 dBi over the operating bandwidth.Figure 2
Simulated return loss of the SIDRA element.Figure 3
Simulated radiation patterns of the SIDRA element at 34.5 GHz.


## 2.1. Antenna Configuration

Figure1 shows the geometry and parameters of the SIDRA element, including the 3D and top views. The antenna element is mainly composed of two parts: an SIDR and a feeding SIW. The SIDR is integrated in the top Rogers RT6010 (εr1 = 10.2, tanδ = 0.0031 at 10 GHz, thickness h1 = 0.635 mm) substrate using the perforation technique with S1 ≥ λ0/10 and S2 ≥ λ0/10 (λ0 is the wavelength at center frequency in free space) [19]. The end-shorted feeding SIW is constructed in the bottom Rogers RT5880 substrate (εr2 = 2.2, tanδ = 0.0013 at 10 GHz, thickness h2 = 0.254 mm) supporting the dominant mode of TE10 within the antenna operating bandwidth. A longitudinal slot with length of Ls and width of Ws is etched on the SIW broad wall in order to couple the energy to the SIDR element. The distance d1 from the center of slot to the SIW short-circuited end is initially chosen to be λg/4 (λg is the guided wavelength) for the maximum coupling [13], and d2 is the slot offset from the centerline of SIW for good matching. The center of the SIDR is the same as the center of the coupling slot, and the SIDRA element operates at the dominant TE111x mode for radiation. The dielectric waveguide model [2, 21] has been employed to evaluate the dimensions of the SIDRA element with the dominant mode for the resonant frequency f0 of 34.5 GHz as
(1)f0=c2πεr1kx2+ky2+kz2,kx=πa,kz=π2h1,kytankyb2=εr1−1k02−ky2,kx2+ky2+kz2=εr1k02,where εr1 is the relative permittivity of the SIDRA, c is the speed of light, h1 is the thickness of the Rogers RT6010 substrate, k0 is the wavenumber in free space, and kx, ky, and kz indicate the wavenumbers along x, y, and z-directions, respectively. Alternatively, the above equations may be used to determine the dimensions of the SIDR for a desired operation frequency. For example, the resonant frequency of f0 = 34.5 GHz corresponds to an SIDR with dimensions a = b = 3.45 mm and h1 = 0.635 mm. The other geometric parameters of the SIDR and the feeding SIW (including Wsiw, D1, P1, Wt, Lt, Wm, D2, S1, and S2) can be obtained from the method of references [19, 20]. Then, these parameters along with Ls and Ws are optimized by using HFSS for good matching and high radiation performance.Figure 1
Structure of the SIDRA element with the longitudinal coupling slot. (a) 3D view and (b) top view. (Ls = 1.6, Ws = 0.2, d1 = 2.15, d2 = 0.55, all in mm).
(a)
(b)


## 2.2. Simulated Results

Figure2 shows the simulated return loss of the SIDRA element. It can be seen that the element exhibits a 10 dB bandwidth of around 10%. The simulated radiation patterns of the SIDRA at 34.5 GHz are presented in Figure 3, and it can be seen that the 3 dB beamwidths in the E(yz)- and H(xz)-planes are about 140° and 70°, respectively. The simulated gain of the element is 4.9–5.6 dBi over the operating bandwidth.Figure 2
Simulated return loss of the SIDRA element.Figure 3
Simulated radiation patterns of the SIDRA element at 34.5 GHz.


## 3. Design of the Linear SIDRAA

### 3.1. Array Configuration

Employing the SIDRA elements as the building blocks, anN × 1 linear SIDRAA with series-feeding structure can be constructed conveniently by means of the PCB technique. As shown in Figure 4, a 4 × 1 SIDRAA example is designed and simulated for Ka-band applications, in which some geometric parameters are set to be Wsiw = 4.2 mm, D1 = 0.4 mm, P1 = 0.6 mm, D2 = 0.5 mm, S1 = 1 mm, S2 = 1.22 mm, Wt = 1.3 mm, Lt = 4.5 mm, Wm = 0.75 mm, Lground = 35 mm, and Wground = 10 mm. The distance between the adjacent SIDRA elements is Lx = λg/2 = 4.4 mm (λg is the guided wavelength in feeding SIW), corresponding to about 0.51λ0 (λ0 is the wavelength at the resonant frequency of the SIDRA in free space). On the other hand, the four elements are positioned at the opposite sides of the feeding-SIW centerline, providing an addition phase shift of π between any two successive slot fields. Thus, the phase difference between the neighboring elements is 2π, and the array elements are excited in phase. The other optimized geometric parameters are given as follows: a=3.4mm, b=3.4mm, Ls=1.6mm, Ws=0.2mm, d1=2.3mm, d2=0.5mm.Figure 4
Structure of the proposed linear SIDRAA.A 4 × 1 SIDRAA prototype was implemented with a two-layer PCB process. Figure5 shows the component parts and the assembled prototype of the fabricated array, in which the SIDRA elements are integrated in a single-side Rogers RT6010 substrate and are combined with the RT5880-based SIW feeding structure by using a little bonding glue.Figure 5
Photograph of fabricated SIDRAA. (a) Series-feeding SIW, (b) SIDRAs, and (c) assembled linear SIDRAA.
(a)
(b)
(c)


### 3.2. Simulated and Measured Results

The return loss of the prototype was measured with the Agilent E8363B vector network analyzer. For testing convenience, a wideband microstrip-SIW taper transition was employed in the design. Figure6 depicts the measured and simulated return losses, and the measured return loss follows the trend of the well-simulated one with a slight deterioration, namely, 9.5 dB at 34.2 GHz, which may be caused by fabrication tolerance and permittivity fluctuation. The SIDRAA offers a measured bandwidth of about 10% (from 32.2 to 35.8 GHz) for 10 dB return loss.Figure 6
Simulated and measured return loss of the proposed SIDRAA.The antenna prototype was also measured in a far-field anechoic chamber. Figure7 describes the measured and simulated normalized radiation patterns at 34.5 GHz, and reasonable agreement between simulation and experiment is obtained. The radiation patterns are broadside and nearly symmetric in both E(yz)- and H(xz)-planes, and the measured 3 dB beamwidths in the two planes are about 140° and 60°, respectively. Meanwhile, the cross-polarization levels less than −18 dB in E-plane and −20 dB in H-plane are observed. Radiation patterns of other frequencies in the passband are also measured and stable and not shown for brevity.Figure 7
Simulated and measured normalized radiation patterns of the proposed SIDRAA at 34.5 GHz. (a)E(yz)-plane and (b) H(xz)-plane.
(a)
(b)The measured gain of the SIDRAA was obtained using the gain transfer method where a standard gain horn was used as a reference, and it is illustrated in Figure8. The measured gain varies between 10.5 and 11.5 dBi over the passband with an average gain of 11.2 dBi. As shown in Figure 8, there is about 0.5 dB drop in the measured gain compared with the simulated one, and the fluctuation of the measured gain is less than 1 dB over the operating bandwidth.Figure 8
Simulated and measured gains of the proposed SIDRAA.


## 3.1. Array Configuration

Employing the SIDRA elements as the building blocks, anN × 1 linear SIDRAA with series-feeding structure can be constructed conveniently by means of the PCB technique. As shown in Figure 4, a 4 × 1 SIDRAA example is designed and simulated for Ka-band applications, in which some geometric parameters are set to be Wsiw = 4.2 mm, D1 = 0.4 mm, P1 = 0.6 mm, D2 = 0.5 mm, S1 = 1 mm, S2 = 1.22 mm, Wt = 1.3 mm, Lt = 4.5 mm, Wm = 0.75 mm, Lground = 35 mm, and Wground = 10 mm. The distance between the adjacent SIDRA elements is Lx = λg/2 = 4.4 mm (λg is the guided wavelength in feeding SIW), corresponding to about 0.51λ0 (λ0 is the wavelength at the resonant frequency of the SIDRA in free space). On the other hand, the four elements are positioned at the opposite sides of the feeding-SIW centerline, providing an addition phase shift of π between any two successive slot fields. Thus, the phase difference between the neighboring elements is 2π, and the array elements are excited in phase. The other optimized geometric parameters are given as follows: a=3.4mm, b=3.4mm, Ls=1.6mm, Ws=0.2mm, d1=2.3mm, d2=0.5mm.Figure 4
Structure of the proposed linear SIDRAA.A 4 × 1 SIDRAA prototype was implemented with a two-layer PCB process. Figure5 shows the component parts and the assembled prototype of the fabricated array, in which the SIDRA elements are integrated in a single-side Rogers RT6010 substrate and are combined with the RT5880-based SIW feeding structure by using a little bonding glue.Figure 5
Photograph of fabricated SIDRAA. (a) Series-feeding SIW, (b) SIDRAs, and (c) assembled linear SIDRAA.
(a)
(b)
(c)


## 3.2. Simulated and Measured Results

The return loss of the prototype was measured with the Agilent E8363B vector network analyzer. For testing convenience, a wideband microstrip-SIW taper transition was employed in the design. Figure6 depicts the measured and simulated return losses, and the measured return loss follows the trend of the well-simulated one with a slight deterioration, namely, 9.5 dB at 34.2 GHz, which may be caused by fabrication tolerance and permittivity fluctuation. The SIDRAA offers a measured bandwidth of about 10% (from 32.2 to 35.8 GHz) for 10 dB return loss.Figure 6
Simulated and measured return loss of the proposed SIDRAA.The antenna prototype was also measured in a far-field anechoic chamber. Figure7 describes the measured and simulated normalized radiation patterns at 34.5 GHz, and reasonable agreement between simulation and experiment is obtained. The radiation patterns are broadside and nearly symmetric in both E(yz)- and H(xz)-planes, and the measured 3 dB beamwidths in the two planes are about 140° and 60°, respectively. Meanwhile, the cross-polarization levels less than −18 dB in E-plane and −20 dB in H-plane are observed. Radiation patterns of other frequencies in the passband are also measured and stable and not shown for brevity.Figure 7
Simulated and measured normalized radiation patterns of the proposed SIDRAA at 34.5 GHz. (a)E(yz)-plane and (b) H(xz)-plane.
(a)
(b)The measured gain of the SIDRAA was obtained using the gain transfer method where a standard gain horn was used as a reference, and it is illustrated in Figure8. The measured gain varies between 10.5 and 11.5 dBi over the passband with an average gain of 11.2 dBi. As shown in Figure 8, there is about 0.5 dB drop in the measured gain compared with the simulated one, and the fluctuation of the measured gain is less than 1 dB over the operating bandwidth.Figure 8
Simulated and measured gains of the proposed SIDRAA.


## 4. Conclusions

A series-fed linear SIDRAA has been proposed and investigated for millimeter-wave applications. The SIDRA elements are integrated conveniently in the substrate using the perforation technique, and the feeding structure can be codesigned and fabricated using the same planar process. The proposed methodology provides a convenient and low-cost strategy for the design of the DRA arrays. A prototype 4 × 1 SIDRAA was designed atKa-band and fabricated with a two-layer PCB technology. The return loss, radiation patterns, and array antenna gain were experimentally studied, and good agreement between the measured and simulated results was observed. The SIDRAA example exhibits a bandwidth of about 10% around 34.5 GHz for 10 dB return loss and stable broadside radiation patterns with an average gain of 11.2 dBi across the band. The proposed linear SIDRAA features the advantages of low cost, low profile, easy manufacture, and convenient integration with other planar circuits, and it can be developed to an N × N planar array for higher antenna gain.



---

*Source: 9672790-2018-04-22.xml*