# Design of a Dual-Band Bidirectional Antenna Using Superellipse-Monopole-Fed Rectangular Ring for IEEE 802.11 a/b/g/n Applications

Authors: Ekajit Khoomwong; Chuwong Phongcharoenpanich
Journal: International Journal of Antennas and Propagation
 (2016)

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## Abstract

This paper presents the design of a dual-band bidirectional ring antenna fed by a superellipse surface probe for 2.4/5 GHz WLAN applications. The Method of Moments (MoM) with RWG basis function was utilized in the study and design processes. A prototype antenna was fabricated successfully with the advantages of simple and low-cost structure. The measured impedance bandwidth of 810 MHz (2.10–2.91 GHz) and 2.39 GHz (3.57–5.96 GHz) is achieved for the first and second band, respectively. The peak gains are also feasible, 4.67 dBi at 2.45 GHz and 7.83 dBi at 5.5 GHz, with bidirectional radiation patterns for both bands. From the experimental field tests, the proposed antenna was suitable for most applications in long and narrow communication sites in 2.4/5 GHz bands as desired. Also, the measured and calculated results were in good agreement.


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## Body

## 1. Introduction

Wireless local area networks (WLAN) recently received widespread attention due to their convenience and cost-effectiveness in many circumstances compared to conventional wired networks. However, in response to the demands of different frequency standards of WLAN, for example, IEEE 802.11b/g (2.4–2.484 GHz) and IEEE 802.11a (5.15–5.35/5.725–5.825 GHz), modern antennas being used in these systems should have multiband features. So far, various elements and techniques have been proposed and implemented on antennas to yield multiband characteristics for WLAN and other wireless communication applications, such as multiradiators or radiating elements [1–3]. Typically, other techniques such as resonant slits, slots, or stub structures [4–11] are also attractive for designing multiband antennas.To serve the demands for long and narrow communication paths, such as streets, tunnels, and subway stations, bidirectional antennas are likely to be the most promising candidates. There are many research topics on bidirectional antennas such as [12–16] that extensively used various ring shapes (i.e., waveguide sections with moderate widths) such as rectangular, circular, and elliptical rings, to force the radiating beams in two opposite directions. Some other techniques are also introduced such as collinear antennas with parasitic wire elements in [17, 18] and a fractal patch antenna with pattern reconfigurable capability in [19].The Method of Moments (MoM) is a frequency-domain technique, which is very useful and usually utilized in computational electromagnetics such as scattering and radiating problems. The process of calculations and its solutions are widely known and improved for many decades, and its evolution was recently overviewed in [20].Generally, there are some drawbacks of using MoM in designing antennas such as limitations in application to radiation or scattering calculations from large structures due to computational resources that scaled with square of unknowns and also a convergence problem of solutions with complex structures, specifically ones that are comprised of various part sizes in the same area. However, there are main advantages of the MoM such as efficient computational resource usage for problems with small surface areas compared to the total volume (e.g., problems with only thin conducting surfaces and free space) and with low complexity in calculation process.Furthermore, many basis functions and computational techniques of MoM have been considered for applying to electromagnetic scattering and radiating problems such as [21–29]. Among these, Rao-Wilton-Glisson (RWG) [21] basis function was still acceptable as one of the most popular basis functions used in antenna analyses and designs. Here, we consider utilizing of the MoM with RWG basis function in the antenna design because it is uncomplicated in the calculation process and suitable for creating a low-cost custom software package. It can be conveniently tailored for this specific structure of antenna with superellipse shapes and can also expedite the automatic parameter sweeping process with moderate accuracy. Although there are many high-end commercial software packages available nowadays, they usually come with high prices. Furthermore, some issues are found in their operations that cannot be solved by users themselves. For instance, in some software packages, one of most common problems is that they do not support inputting of a non-one-to-one analytical function directly (e.g., a superellipse curve family) due to complexity in automatic mesh-generation process and thus impede or sometimes obstruct the parameter sweeping and designing processes.In this paper, we provide the details of analyses, comparisons, operational mechanism explanations, and discussions of a rectangular ring antenna proposed in [30], which is excited by a superellipse surface probe to provide dual-band characteristic for 2.4–2.484 GHz and 5.15–5.35/5.725–5.825 GHz WLAN applications with bidirectional radiation patterns enforced by the ring. The superellipse or Lamé curve is a key function employed to investigate and achieve dual- and wideband attribute. The study and design of the antenna are mainly performed by utilizing the Method of Moments with the Rao-Wilton-Glisson basis function (MoM-RWG) [21].


## 2. Antenna Structure and Parameters

An antenna structure and its parameters are illustrated in Figure1 where a and b are semiaxis lengths of the superellipse surface probe along the y- and z-direction, respectively. The surface probe is attached at the tip of a thin feeding probe with height, h. The rectangular ring surrounding the probe has width, height, and length of W, H, and L, respectively.Figure 1
An antenna structure and its parameters.As mentioned above, the superellipse or Lamé curve is a key function to be used for generating different shapes of the surface probe, so its geometrical function should be stated clearly with related parameters on they-z plane, as in (1)yaν+zbν=1.The parameterν is a nonzero positive value, sometimes called a squareness parameter since it tends to make the curve nearly square while its value is approaching infinity. It is possible that (1) can be solved into explicit parametric form of coordinates (y,z) as in (2); then some basic shapes of the surface probe can be generated by using (2), which are typically depicted in Figure 2:(2)y=a·ψβcos⁡β,z=b·ψβsin⁡β,where ψβ=sin⁡βν+cos⁡βν-1/νand β is an angle ranging from 0 to 2π for a full circumference.Figure 2
Typical basic shapes of the surface probe.


## 3. Antenna Design and Simulation

### 3.1. Formulation of the Method of Moments

As previously stated, the Method of Moments with RWG basis function is utilized in the study and design processes of the antenna. By considering the electric field integral equation (EFIE) under open boundary condition, we may approximate the surface current density on antenna’s metallic body in terms of RWG basis function, as in(3)J-≅∑n=1NI-nf-nr-,where J- is the surface current density, f-n is the RWG basis function, and I-n is an expansion coefficient of current density. When the antenna structure is discretized by triangulation and incorporating with (3), the EFIE can be approximated and solved for I-n in form of matrix equation as (4)ZmnI-n=V-m,where Zmn is an impedance matrix of size M×N. [I-n] and [V-m] are the expansion coefficient vector and the applied voltage source vector, respectively. More detailed formulations and other parameter descriptions can be found in [21].


### 3.2. Triangulation of the Antenna Structure

As insisted earlier, the calculation domain is required to be discretized by triangulation to implement the Method of Moments with RWG basis function. Roughly, there are two categories of triangulation process, nonuniform and uniform type. For instance, the Delaunay triangulation is the nonuniform type dealing with some random functions and optimization techniques thus may require extensive computation resources, but it can be applied to any shapes of structures. On the other hand, the uniform type triangulation is much simpler and straight forward requiring only predefined parametric formulas of coordinates, but it may handle only simple geometric structures. Since in this paper the antenna is comprised of simple structures such as a rectangular ring and a superellipse surface probe, it is convenient to employ the uniform-type triangulation. For the superellipse surface probe, (2) can be rewritten in discretized form as (5)yi=ak·ψβicos⁡βi,zi=bk·ψβisin⁡βi,where βi is a discretized angle along the circumference of the shape. Thus βi=iΔβ, where i=0,1,2,…,Nβ and Δβ= 2π/Nβ. In the radial direction, step layers are defined by ak=kΔa and bk=kΔb, where k=0,1,2,…,Nr, Δa=a/Nr, and Δb=b/Nr. For the rectangular ring, the similar approach of triangulation can be applied. As a general example, a triangulated antenna structure with a=b= 1.5 cm, ν = 0.75 cm, W= 3 cm, H = 2 cm, L = 1.5 cm, hf = 0.3 cm, Nβ = 32, and Nr = 6 is shown in Figure 3.Figure 3
An example of triangulated antenna structure.


### 3.3. Design and Simulation Processes

In order to design the antenna, it is important to know initial antenna parameters to be used. Then the parametric study can be performed to evaluate the optimal or suitable sets of antenna parameters. Most of initial parametric values are selected based on classical analytic formulas.For the ring element of the antenna, the design formula for a rectangular waveguide is utilized to obtain the dimensions,W and H, as follows: (6)W=3×1082fc,H≤KH×W2,where fc is the cutoff frequency of a rectangular waveguide.The coefficientKH is a constant factor, typically in the range from 0.5 to 1.5, which increases the waveguide’s height from the optimal bandwidth case to accommodate a large surface probe. For the surface probe, due to a variety of parameters affecting the resonant length, a simple rule of electrical length is adapted, which is relating to the feeding probe parameters as (7)a+2b+h≅λ4,where λ is the wavelength of a desired operating frequency.From (6) and (7), we use the center operating frequency of the first band, that is, 2.45 GHz; thus the initial parameters are predicted as follows: W = 72 mm, H = 72 mm, L = 22 mm, a = 11 mm, b = 11 mm, and h = 1.75 mm. Please note that all parameters above are only approximate dimensions, not accounting for the coupling effect of antenna elements. The suitable parameters are to be evaluated by parametric study.In addition to the simulation process, the triangulation related parameters of the antenna structure, such asNβ and Nr, are estimated by a convergence criterion as the shortest edge element’s length (ln), defined in [21], should be <λ/5 of the highest frequency. The criterion is specifically based on the MoM simulations of the proposed antenna, and the graphical results and discussions are omitted here for the sake of brevity.


### 3.4. Parametric Study and Design Results

The parametric study is performed by first varying the parameterν to investigate the effect of superellipse probe shapes on the impedance characteristic of the antenna, while other parameter values are fixed as mentioned above.Figure4 depicts results of impedance characteristics for typical values of ν at two frequencies, f1 = 2.5 GHz and f2 = 5.5 GHz, near the centers of both operating bands. It is observed that the star-shaped probes (ν < 1, see Figure 5 for shapes) exhibit high resistances, especially at the higher band (f2). For the reactance characteristics, the highly fluctuating values, that is, from capacitive to inductive, can be obviously observed at f2, whereas the low disturbance ones can be seen at f1 in capacitive region. When ν≥1, the impedance characteristics start to converge to some reasonable points. Specifically, for ν≥ 10, stable impedances can be observed.Figure 4
Impedance characteristics versus typical values ofν.Figure 5
Bandwidth characteristics versus typical values ofν.Figure5 summarizes the results of impedance bandwidth characteristics for typical values of ν along with some images of probe shapes. It is observed that, for the frequency range of 1 to 6 GHz, a star-shaped probe possesses single-band property since it tends to increase the resistance when ν is decreased, and it has more significant effects on the second operating band. Thus the star-shaped probe is more suitable for single narrow- or single wideband applications in this specific configuration. When ν≥ 1.0, broader impedance bandwidths can be achieved because of lower resistance and more inductive loading effect of the surface probe diminishing the capacitive reactance characteristic of the antenna. Finally, it is obviously remarked that to obtain a dual-band characteristic, the value of ν greater than 2 should be applied. From now on, ν = 18 is used since it has stable impedance characteristic near the 2.4/5-GHz bands as required and yields a good compromising point and also has an advantage of simple shape for ease of fabrication process with lower shaping tolerance.Figures6 and 7 illustrate the effects of main parameters, that is, a,b,W,H, and L, on the magnitude of S11 (S11) curves at −10 dB level. In the simulations, while one parameter is varying other ones are fixed at their initial parametric values.Figure 6
(a) Characteristics ofS11 by varying a. (b) Characteristics of S11 by varying b.
(a) (b)Figure 7
(a) Characteristics ofS11 by varying W. (b) Characteristics of S11 by varying H. (c) Characteristics of S11 by varying L.
(a) (b) (c)Figures6(a) and 6(b) show S11 characteristics by varying sizes of the surface probe, a and b. In Figure 6(a), the dual-band characteristic is obtained at a = 9 and 11 mm particularly for the 2.4-GHz band and nearly achieved for the 5-GHz band.Also, in Figure6(b), it is observable that good dual-band characteristic is obtainable near b = 13 and 15 mm. When both of the parameters are considered at the same time it is found that the suitable values of a and b are 9 mm and 14 mm, respectively, and to be set as new initial parametric values.Figures7(a)–7(c) depict S11 by varying dimensions of the ring, W,H, and L. In Figure 7(a), W affects the matching frequency and bandwidth, more significantly for the higher band. At this stage, a good compromising point is W = 64 mm.Then,W = 64 mm is used as a new fixed parametric value, leading to the results as in Figure 7(b). Obviously, when H is higher the matching is more degraded for the first band, and the operating frequency is slightly lower for the second band. For Figure 7(c), the matching of the first band is affected significantly by varying L of the ring. It is obvious that a new parametric value is better near L = 20 mm.At this point, to verify that the selected value ofν=18 can still provide a good compromise between the characteristic of being dual-band and the impedance matching near the higher band as depicted in Figure 8 by varying typical values of ν. It is noticeable that, at ν=10, the dual-band characteristic is degraded as it tends to be excessively wide for the specific bandwidth requirement of this paper. Meanwhile, as ν→∞ (i.e., a perfect rectangular probe), the impedance matching characteristic is worsened near the higher frequency range since the sharp corners of the rectangular surface probe affect the current flow at the probe edges more than the round and smooth ones, which often seen in applications of microwave circuits as beveled or round edge transitions. Therefore the selected round rectangle shape (ν=18) can noticeably improve the impedance matching near the higher band.Figure 8
Characteristics ofS11 by varying ν.In addition to the parametric study above, the impedance matching can be further adjusted by fine tuning the parameterh, that is, height of the feeding tip. After iterating in some more parametric study processes, it is found that the optimal set of parameters can be obtained as in Table 1 and the final triangulated antenna model is illustrated in Figure 9. It should be noted that the rectangular ring model has small bevels at its corners to equivalently account for roundness of the folded copper strip to form the ring, that is, following the plan in the fabrication process.Table 1
Optimal set of parameters.
Parameter Value a 9.1 mm b 14.0 mm ν 18 h 1.7 mm W 66 mm H 67 mm L 23 mmFigure 9
The final triangulated antenna structure.


### 3.5. Operation Mechanism

To further investigate the main working principle of the proposed antenna, more parametric study and surface current density are considered. The final model and parametric values obtained from Section3.4 are used to illustrate its mechanism of operation.First, to proceed with more parametric study process we consider an exchange of the superellipse surface probe with a simple linear-wire probe having a resonant length of about quarter wavelength (λ/4) of the first operating frequency f1, which is related to the original feeding models proposed in [12, 13] and more recent literatures in [14–16]. The parametric study results of S11 of the final rectangular ring with the exchanged linear-wire probe are shown in Figure 10, along with S11 from the proposed final model from Figure 9. It is apparent that excitation by the linear-wire cannot generate the higher mode (i.e., higher frequency) of operation for this antenna configuration in the frequency range from 1 to 6 GHz. Thus the linear-wire probe mainly supports only single band of operation in this case when compared with the final proposed structure.Figure 10
S 11 of linear-wire probe versus the proposed model.Second, to further explain the dual-band characteristic of the proposed antenna the surface current densities on its body are examined as shown in Figures11 and 12 for the first (f1) and second (f2) frequency of 2.45 GHz and 5.5 GHz, respectively. As depicted in Figure 11, the current density at f1 = 2.45 GHz reflects the fundamental mode of operation with one set of current maximum and minimum point on the rectangular ring and also on the feeding surface probe itself. In Figure 12, the current density at f2 = 5.5 GHz reveals that the higher mode of resonant operating frequency occurs, obviously with two sets of current maxima and minima on the rectangular ring and also with noticeable different patterns of current near the surface probe by comparing with that of the first frequency.Figure 11
Current density on the proposed model at 2.45 GHz.Figure 12
Current density on the proposed model at 5.5 GHz.


## 3.1. Formulation of the Method of Moments

As previously stated, the Method of Moments with RWG basis function is utilized in the study and design processes of the antenna. By considering the electric field integral equation (EFIE) under open boundary condition, we may approximate the surface current density on antenna’s metallic body in terms of RWG basis function, as in(3)J-≅∑n=1NI-nf-nr-,where J- is the surface current density, f-n is the RWG basis function, and I-n is an expansion coefficient of current density. When the antenna structure is discretized by triangulation and incorporating with (3), the EFIE can be approximated and solved for I-n in form of matrix equation as (4)ZmnI-n=V-m,where Zmn is an impedance matrix of size M×N. [I-n] and [V-m] are the expansion coefficient vector and the applied voltage source vector, respectively. More detailed formulations and other parameter descriptions can be found in [21].


## 3.2. Triangulation of the Antenna Structure

As insisted earlier, the calculation domain is required to be discretized by triangulation to implement the Method of Moments with RWG basis function. Roughly, there are two categories of triangulation process, nonuniform and uniform type. For instance, the Delaunay triangulation is the nonuniform type dealing with some random functions and optimization techniques thus may require extensive computation resources, but it can be applied to any shapes of structures. On the other hand, the uniform type triangulation is much simpler and straight forward requiring only predefined parametric formulas of coordinates, but it may handle only simple geometric structures. Since in this paper the antenna is comprised of simple structures such as a rectangular ring and a superellipse surface probe, it is convenient to employ the uniform-type triangulation. For the superellipse surface probe, (2) can be rewritten in discretized form as (5)yi=ak·ψβicos⁡βi,zi=bk·ψβisin⁡βi,where βi is a discretized angle along the circumference of the shape. Thus βi=iΔβ, where i=0,1,2,…,Nβ and Δβ= 2π/Nβ. In the radial direction, step layers are defined by ak=kΔa and bk=kΔb, where k=0,1,2,…,Nr, Δa=a/Nr, and Δb=b/Nr. For the rectangular ring, the similar approach of triangulation can be applied. As a general example, a triangulated antenna structure with a=b= 1.5 cm, ν = 0.75 cm, W= 3 cm, H = 2 cm, L = 1.5 cm, hf = 0.3 cm, Nβ = 32, and Nr = 6 is shown in Figure 3.Figure 3
An example of triangulated antenna structure.


## 3.3. Design and Simulation Processes

In order to design the antenna, it is important to know initial antenna parameters to be used. Then the parametric study can be performed to evaluate the optimal or suitable sets of antenna parameters. Most of initial parametric values are selected based on classical analytic formulas.For the ring element of the antenna, the design formula for a rectangular waveguide is utilized to obtain the dimensions,W and H, as follows: (6)W=3×1082fc,H≤KH×W2,where fc is the cutoff frequency of a rectangular waveguide.The coefficientKH is a constant factor, typically in the range from 0.5 to 1.5, which increases the waveguide’s height from the optimal bandwidth case to accommodate a large surface probe. For the surface probe, due to a variety of parameters affecting the resonant length, a simple rule of electrical length is adapted, which is relating to the feeding probe parameters as (7)a+2b+h≅λ4,where λ is the wavelength of a desired operating frequency.From (6) and (7), we use the center operating frequency of the first band, that is, 2.45 GHz; thus the initial parameters are predicted as follows: W = 72 mm, H = 72 mm, L = 22 mm, a = 11 mm, b = 11 mm, and h = 1.75 mm. Please note that all parameters above are only approximate dimensions, not accounting for the coupling effect of antenna elements. The suitable parameters are to be evaluated by parametric study.In addition to the simulation process, the triangulation related parameters of the antenna structure, such asNβ and Nr, are estimated by a convergence criterion as the shortest edge element’s length (ln), defined in [21], should be <λ/5 of the highest frequency. The criterion is specifically based on the MoM simulations of the proposed antenna, and the graphical results and discussions are omitted here for the sake of brevity.


## 3.4. Parametric Study and Design Results

The parametric study is performed by first varying the parameterν to investigate the effect of superellipse probe shapes on the impedance characteristic of the antenna, while other parameter values are fixed as mentioned above.Figure4 depicts results of impedance characteristics for typical values of ν at two frequencies, f1 = 2.5 GHz and f2 = 5.5 GHz, near the centers of both operating bands. It is observed that the star-shaped probes (ν < 1, see Figure 5 for shapes) exhibit high resistances, especially at the higher band (f2). For the reactance characteristics, the highly fluctuating values, that is, from capacitive to inductive, can be obviously observed at f2, whereas the low disturbance ones can be seen at f1 in capacitive region. When ν≥1, the impedance characteristics start to converge to some reasonable points. Specifically, for ν≥ 10, stable impedances can be observed.Figure 4
Impedance characteristics versus typical values ofν.Figure 5
Bandwidth characteristics versus typical values ofν.Figure5 summarizes the results of impedance bandwidth characteristics for typical values of ν along with some images of probe shapes. It is observed that, for the frequency range of 1 to 6 GHz, a star-shaped probe possesses single-band property since it tends to increase the resistance when ν is decreased, and it has more significant effects on the second operating band. Thus the star-shaped probe is more suitable for single narrow- or single wideband applications in this specific configuration. When ν≥ 1.0, broader impedance bandwidths can be achieved because of lower resistance and more inductive loading effect of the surface probe diminishing the capacitive reactance characteristic of the antenna. Finally, it is obviously remarked that to obtain a dual-band characteristic, the value of ν greater than 2 should be applied. From now on, ν = 18 is used since it has stable impedance characteristic near the 2.4/5-GHz bands as required and yields a good compromising point and also has an advantage of simple shape for ease of fabrication process with lower shaping tolerance.Figures6 and 7 illustrate the effects of main parameters, that is, a,b,W,H, and L, on the magnitude of S11 (S11) curves at −10 dB level. In the simulations, while one parameter is varying other ones are fixed at their initial parametric values.Figure 6
(a) Characteristics ofS11 by varying a. (b) Characteristics of S11 by varying b.
(a) (b)Figure 7
(a) Characteristics ofS11 by varying W. (b) Characteristics of S11 by varying H. (c) Characteristics of S11 by varying L.
(a) (b) (c)Figures6(a) and 6(b) show S11 characteristics by varying sizes of the surface probe, a and b. In Figure 6(a), the dual-band characteristic is obtained at a = 9 and 11 mm particularly for the 2.4-GHz band and nearly achieved for the 5-GHz band.Also, in Figure6(b), it is observable that good dual-band characteristic is obtainable near b = 13 and 15 mm. When both of the parameters are considered at the same time it is found that the suitable values of a and b are 9 mm and 14 mm, respectively, and to be set as new initial parametric values.Figures7(a)–7(c) depict S11 by varying dimensions of the ring, W,H, and L. In Figure 7(a), W affects the matching frequency and bandwidth, more significantly for the higher band. At this stage, a good compromising point is W = 64 mm.Then,W = 64 mm is used as a new fixed parametric value, leading to the results as in Figure 7(b). Obviously, when H is higher the matching is more degraded for the first band, and the operating frequency is slightly lower for the second band. For Figure 7(c), the matching of the first band is affected significantly by varying L of the ring. It is obvious that a new parametric value is better near L = 20 mm.At this point, to verify that the selected value ofν=18 can still provide a good compromise between the characteristic of being dual-band and the impedance matching near the higher band as depicted in Figure 8 by varying typical values of ν. It is noticeable that, at ν=10, the dual-band characteristic is degraded as it tends to be excessively wide for the specific bandwidth requirement of this paper. Meanwhile, as ν→∞ (i.e., a perfect rectangular probe), the impedance matching characteristic is worsened near the higher frequency range since the sharp corners of the rectangular surface probe affect the current flow at the probe edges more than the round and smooth ones, which often seen in applications of microwave circuits as beveled or round edge transitions. Therefore the selected round rectangle shape (ν=18) can noticeably improve the impedance matching near the higher band.Figure 8
Characteristics ofS11 by varying ν.In addition to the parametric study above, the impedance matching can be further adjusted by fine tuning the parameterh, that is, height of the feeding tip. After iterating in some more parametric study processes, it is found that the optimal set of parameters can be obtained as in Table 1 and the final triangulated antenna model is illustrated in Figure 9. It should be noted that the rectangular ring model has small bevels at its corners to equivalently account for roundness of the folded copper strip to form the ring, that is, following the plan in the fabrication process.Table 1
Optimal set of parameters.
Parameter Value a 9.1 mm b 14.0 mm ν 18 h 1.7 mm W 66 mm H 67 mm L 23 mmFigure 9
The final triangulated antenna structure.


## 3.5. Operation Mechanism

To further investigate the main working principle of the proposed antenna, more parametric study and surface current density are considered. The final model and parametric values obtained from Section3.4 are used to illustrate its mechanism of operation.First, to proceed with more parametric study process we consider an exchange of the superellipse surface probe with a simple linear-wire probe having a resonant length of about quarter wavelength (λ/4) of the first operating frequency f1, which is related to the original feeding models proposed in [12, 13] and more recent literatures in [14–16]. The parametric study results of S11 of the final rectangular ring with the exchanged linear-wire probe are shown in Figure 10, along with S11 from the proposed final model from Figure 9. It is apparent that excitation by the linear-wire cannot generate the higher mode (i.e., higher frequency) of operation for this antenna configuration in the frequency range from 1 to 6 GHz. Thus the linear-wire probe mainly supports only single band of operation in this case when compared with the final proposed structure.Figure 10
S 11 of linear-wire probe versus the proposed model.Second, to further explain the dual-band characteristic of the proposed antenna the surface current densities on its body are examined as shown in Figures11 and 12 for the first (f1) and second (f2) frequency of 2.45 GHz and 5.5 GHz, respectively. As depicted in Figure 11, the current density at f1 = 2.45 GHz reflects the fundamental mode of operation with one set of current maximum and minimum point on the rectangular ring and also on the feeding surface probe itself. In Figure 12, the current density at f2 = 5.5 GHz reveals that the higher mode of resonant operating frequency occurs, obviously with two sets of current maxima and minima on the rectangular ring and also with noticeable different patterns of current near the surface probe by comparing with that of the first frequency.Figure 11
Current density on the proposed model at 2.45 GHz.Figure 12
Current density on the proposed model at 5.5 GHz.


## 4. Measurement Results and Discussions

To validate the design of the MoM-RWG, a prototype antenna was fabricated with the optimal set of parameters from the preceding section, as shown in Figure13. The rectangular ring and superellipse surface probe were created by directly cutting from a thin copper sheet, which were found low-cost and practical for arbitrary sizes of the ring and various shapes of the surface probe.Figure 13
Photograph of a prototype antenna.In Figure14, the measured results of S11 are compared with ones from the calculations. The results are found in good agreement except the slight shift near the second band. The discrepancies may arise from the SMA and probe feeding.Figure 14
Calculated and measured results ofS11.From Figure14, the measured impedance bandwidth (S11 ≤ −10 dB) of the first band is 810 MHz (2.10–2.91 GHz) with S11 matching −27.39 dB at the center frequency, 2.45 GHz. For the second band, the measured impedance bandwidth is 2.39 GHz (3.57–5.96 GHz) with the S11 matching −25.44 dB at the center frequency, 5.5 GHz.Finally, the results of far-field characteristics such as radiation patterns and gains are compared between the calculation and measurement. The radiation patterns are compared as shown in Figures15 and 16 to confirm the bidirectional property of the antenna. Figure 15 shows normalized radiation patterns in the E-plane at the frequencies of 2.45 and 5.5 GHz. It is noticeable that the main beam directions are pointing to almost the same angle of 75 degrees.Figure 15
Radiation patterns iny-z plane (E-plane).Figure 16
Radiation patterns inx-y plane (H-plane).Figure16 shows normalized radiation patterns in the H-plane with the two main beams directing along the ring’s apertures. From Figures 15 and 16, it is evident that the proposed antenna has bidirectional property as desired. Since the radiation patterns have slightly tilt-angle characteristics with upward angle about 15 degrees, the proposed antenna is most suitable for the ceiling-mounted or wall-mounted installation.To compare the peak gains and total efficiencies (ηtotal) of the antenna from the calculation and measurement, some frequencies in both operating bands were selected and measured as shown in Table 2. Please note that all the calculated gains and efficiencies are accounting only for the reflection efficiency since all conductor parts are assumed PEC. From the results, the calculated and measured peak gains are agreed fairly well. However, there are some discrepancies due to the PEC structure assumed in the calculations and also arise from some tolerances in the fabrication process.Table 2
Comparison of peak gain and antenna efficiency.
Frequency (GHz) Peak Gain (dBi) Efficiency (ηtotal) Calculated Measured Calculated Measured 2.4 4.64 4.52 0.992 0.894 2.45 4.86 4.67 0.996 0.885 2.5 4.97 4.73 0.998 0.879 5.2 7.11 7.10 0.997 0.921 5.5 7.92 7.83 0.994 0.909 5.8 7.98 7.85 0.962 0.875Finally, Table3 shows the comparison of typical measured characteristics of the proposed antenna versus some other models that have bidirectional radiation patterns for specific purpose in the 2.4 GHz and/or 5 GHz WLAN bands. The first two models, #1 and #2, are for the single-band operation at 2.4 GHz with the features of dual polarization. It is noticeable that the structure in [31] has the lowest gain due to the circularly polarized radiation. For the dual-band characteristics, #3 to #5, the model in [33, 34] has similar configurations with some modifications of radiating elements. They provide high average gains of both bands. However, both of them are not covering the lower range of the 5-GHz band and having larger antenna size because of the ground planes. From the comparison above, it is obvious that the proposed antenna has the main advantage of covering the entire 2.4 GHz and 5 GHz bands with sufficient gains and moderate size.Table 3
Comparison of some bidirectional antennas used in the 2.4 GHz and/or 5 GHz WLAN bands.
Number Ref. model Freq. band type Absolute bandwidth &frequency range (GHz) Peak gain (dBi)at specific frequency Overall sizeW×L×H in mm 2.4 GHz-band 5 GHz-band 2.45 GHz 5.2 GHz 5.5 GHz 5.8 GHz 1 [31] Single 0.23 (2.29–2.52) N/A 3.8 N/A N/A N/A 77  ×  142 × 77 2 [32] Single 0.32 (2.32–2.64) N/A 9.6 N/A N/A N/A 50  ×  160 × 50 3 [33] Dual 0.28 (2.25–2.53) 0.51 (5.47–5.98) 5.75 N/A 7.00 8.50 200  ×  200 × 65 4 [34] Dual 0.42 (2.22–2.64) 1.16 (5.25–6.41) 5.95 N/A 6.90 8.80 200  ×  200 × 80 5 Proposed Dual 0.81 (2.10–2.91) 2.39 (3.57–5.96) 4.67 7.10 7.83 7.85 66  ×  23 × 67


## 5. Conclusions

In this paper, we have presented the design of a dual-band bidirectional ring antenna that is excited by a superellipse surface probe for applications in 2.4 and 5 GHz WLAN bands. In the design processes, the Method of Moments (MoM) with RWG basis function was adopted. A prototype antenna was fabricated by forming a thin copper sheet, which has the advantages of simple and low-cost structure.The measured impedance bandwidth of 810 MHz (2.10–2.91 GHz) and 2.39 GHz (3.57–5.96 GHz) is achieved for the first and second band, respectively. The matching characteristics onS11 curves are −27.39 dB and −25.44 dB at the center frequency of the first band, 2.45 GHz, and the second band, 5.5 GHz, respectively. The peak gains are also found applicable, 4.67 dBi at 2.45 GHz and 7.83 dBi at 5.5 GHz for WLAN applications, with bidirectional radiation patterns for both bands. In addition, the radiation patterns of both operating bands are slightly shifted upward near the same 15° tilt-angle with respect to the horizontal plane, which is suitable for ceiling- and wall-mounted installations.From the experimental field tests, the proposed antenna was found useful for most applications in long and narrow communication sites in 2.4 and 5 GHz bands as desired. The measured and calculated results were found in good agreement with some discrepancies which arose from the fabrication errors such as the SMA connector and surface probe joining.



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*Source: 9368904-2016-11-07.xml*