# Trifrequency Reconfigurable Linear Irregular Array with Beam Deflection Capability in X/Ku/Ka-Bands

Authors: Ming Li; Haiping Wei; Jiahao Zhao; Qingchang Tao
Journal: International Journal of Antennas and Propagation
 (2020)

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## Abstract

This paper proposes a trifrequency reconfigurable antenna (FRA), which can work in the X-band, Ku-band, and Ka-band, by controlling only two RF MEMS switches. The antenna element has a frequency ratio beyond 3 : 1 and provides a good candidate for the frequency reconfigurable antenna array, since the size of the antenna is reduced by loading multiple metal shorting holes between the antenna radiating surface and the ground plate, and the overall size is only 0.14λX × 0.35λX (λX is the free-space wavelength at 8.6 GHz). Based on the proposed FRA element, a 1 × 16 linear irregular frequency reconfigurable antenna array (FRAA) with beam deflection ability is designed, which effectively addresses the element spacing problem in the optimization of the array. In addition, the close-coupling in X-band and the grating lobe caused by the long distance of array element spacing in Ka-band are comprehensively considered. With uniform amplitude feeding network, the sidelobe level is below −15 dB under beam deflection. Moreover, both FRA elements and FRAA prototypes have been fabricated and measured to verify their superiority. Good agreements are obtained between simulated and measured results, which indicates that the antenna has potential application in the future multifrequency wireless communication and intelligent radar anti-interference fields.


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## Body

## 1. Introduction

\With the rapid development of wireless communication and intelligent radar technology, antennas have been desired to be multifunctional, intelligent, miniaturized, and low cost. However, traditional single-function antenna is difficult to satisfy these new requirements. Increasing the number of single-function antennas to implement multifunctional RF-integrated equipment can inevitably lead to many problems; that is, the increase in the area occupied by the antenna makes it difficult to achieve miniaturization and the stealth performance of the aircraft. Moreover, the increase in equipment weight and cost becomes the main obstacle in the green application and development of the multifunctional antenna. In such case, reconfigurable antenna, by mechanically or electrically changing its architecture, can effectively change its performance characteristics (resonant frequency, radiation pattern, polarization, etc.) [1] and therefore provides a promising candidate to realize intelligent RF front end.Frequency reconfigurable antenna (FRA) has the advantages of high spectrum utilization and strong anti-interference ability in the frequency domain. The resonant frequency can be adjusted according to the working environment. Previously, FRA has received widespread attention from the industrial sector and academia. The characteristics of FRA have been verified and FRAs implemented in various forms, including dipole [2], slot [3, 4], Vivaldi [5], patch [6, 7], fractal [8], pixels [9–11], and reflection array [12], with their applications in radar [13], wireless communication [4, 9], cognitive radio [2, 5], aircraft conformal antenna [11], and satellite communication and navigation [7, 12].From the previous research mentioned previously, we know that the previously proposed FRA element mostly focused on the low-frequency band, and the frequency ratio was generally less than 3 : 1 [2–11]. However, relatively few reconfigurable antennas for Ku or higher frequency bands and frequencies greater than 3 : 1 have been put forward [14]. In response to the requirements of wireless communications, remote sensing, and radar for frequency reconfigurable antenna arrays, a number of researches have also been carried out [14–19]. However, the half-wavelength constraint condition of the spacing between the traditional phased array antenna elements poses great challenges to the layout of the frequency reconstructed antenna array. Arraying in a low-frequency state makes the high-frequency spacing too large, but in a high-frequency state it can cause coupling in the low frequency [16, 19]. Therefore, trifrequency FRAA with beam deflection capability covering Ka-band and frequency ratio greater than 3 : 1 is urgently desired.In this paper, a novel trifrequency X/Ku/Ka FRA element is proposed, and a 1 × 16 linear irregular FRAA is designed based on this element. The proposed design has the following advantages: (1) The FRA unit uses two RF MEMS switches to achieve frequency switching in X-band, Ku-band, and Ka-band, and a frequency ratio of 3.57 : 1 is achieved. (2) The loading of multiple shorting metal holes between the radiation patch and the ground plate reduces the overall size of the FRA to 0.14λX × 0.35λX (λX is the free-space wavelength at 8.6 GHz), at the lowest frequency. Thus, it provides a good candidate for the optimization of the element spacing of the FRAA. (3) Improved fruit-fly optimization algorithm (FOA) together with MATLAB-HFSS cosimulation is used to optimize the element spacing of a 1 × 16 linear irregular FRAA with beam deflection ability in the same direction in X-band, Ku-band, and Ka-band. The tough spacing problem in the optimization of the traditional FRAA is effectively addressed by the proposed method in this paper, and the sidelobe levels of different frequency reconfigurability states are all lower than −15 dB.This paper is organized as follows. In Section2, the design of the FRA element is introduced, and its frequency reconfigurable performance is simulated and analysed. In Section 3, the design and optimization of linear irregular frequency reconfigurable arrays are discussed in detail, and the sidelobe levels of equally spaced antenna arrays are compared and analysed. The production and testing of FRA and FRAA prototypes are introduced in Section 4. Finally, conclusion is drawn in Section 5.


## 2. Design of FRA Element

### 2.1. Basic Structure Design

It is well known that the operating frequency of the antenna depends on the equivalent electrical length of the radiator. Generally speaking, the longer the equivalent electrical length, the lower the operating frequency. Motivated by that, an easy way to achieve multiband reconfigurable antenna can start from the smallest size corresponding to the highest frequency, that is, by connecting additional patches with switches and by adjusting the overall size of the antenna by controlling the switches’ On and Off state. According to this principle, the basic structure of the proposed FRA element is shown in Figure1. Three multiscale microstrip patches are printed on the Rogers 4350B dielectric substrate, whose dielectric constant is 3.66, loss tangent is 0.004, and thickness is 0.508 mm. It is fed by using a coaxial line. When designing the basic structure of the FRA element, the two red rectangles of 2.0 mm × 1.1 mm in Figure 1 indicate that RF switches are replaced by copper plates to adjust the antenna topology. The connection or disconnection of the metal strip is equivalent to the On/Off function of the switch. When S1 is On and S2 is Off, the FRA element can work in X-band. When S1 is Off and S2 is On, the FRA element can work in Ku-band. Otherwise, when both S1 and S2 switches are Off, the FRA element will work in Ka-band. Figure 2 shows the optimized process of the size of the three radiators.Figure 1
Geometry of the proposed FRA element. (a) 3D view. (b) Front view (unit (mm):a = 17.0, b = 34.0, m1 = n1 = 2.3, m2 = 1.0, n2 = 5.0, m3 = n3 = 5.0, d = 0.4, p=1.0, L1 = 1.1, and L2 = 2.0).
(a)(b)Figure 2
Optimized results of the three radiators. (a) Ka-band. (b) Ku-band. (c) X-band.
(a)(b)(c)In addition, the antenna is utilized to construct a linear array working at the Ka-band (highest), which limits the size of the antenna element in the array dimension. The recent research shows that miniaturization of microstrip antennas can be achieved by shorting surfaces, shorting strips, or shorting probes [6, 20]. Inspired by that, five metal shorting holes between the microstrip patch and the ground plate are employed to reduce the overall antenna size in this paper, and through the optimization of the diameter and spacing of the metal shorting holes, a significant reduction in bandwidth is avoided, the optimized results of which are shown in Figure 2(c).Figure3 shows the simulation results of reflection coefficients at different frequency reconstruction states. It can be seen that FRA can work in X-band, Ku-band, and Ka-band. Taking the reflection coefficient less than −10 dB as the reference, the impedance bandwidth and center frequency are 106 MHz (8.6 GHz), 230 MHz (17.1 GHz), and 1900 MHz (31.1 GHz), respectively. Moreover, the reconstruction frequency ratio of the FRA reaches 3.61 : 1, and the size is 5.0 mm × 12.3 mm, which is only 0.143λX × 0.353λX, at the lowest frequency (8.6 GHz).Figure 3
Simulation results of reflection coefficients at different frequency reconstruction states.


### 2.2. FRA Integrated RF MEMS Switch Design

The coplanar waveguide capacitive MEMS switch proposed by the author’s research group is used. The substrate material is high-resistance silicon. The insulating layer is formed by thermal oxidation of a silicon substrate, whose main material component is silicon oxide. A detailed description of the switch can be found in [21].The structure of the FRA integrated RF MEMS switch is shown in Figure4. Based on the antenna structure in the ideal switching state, a prepreg layer for lamination is added under the ground plate, and a Rogers 4350B dielectric substrate with a thickness of 0.508 mm is introduced, which is used to route the coaxial feed port and the DC bias lines of the RF MEMS switches. Gold wire with 20 um diameter is used to bond RF MEMS switches and microstrip patches.Figure 4
Structure of the FRA integrated RF MEMS switches.The transition structure of the RF MEMS switch integrated into the microstrip antenna is shown in Figure5, and the transition structures of the switches S1 and S2 have different sizes as shown in Table 1. The CPW center signal line of the RF MEMS switch is connected to the microstrip antenna radiation patch through a piece of trapezoidal gradient impedance transformation structure to achieve impedance matching. In addition, a rectangular slot for switch installation is designed with a gap of Fc = 75 μm, an area of 1.35 mm × 1.25 mm (Wc × Lc), and a depth of 410 μm.Figure 5
Transition structure of RF MEMS switch integrated in microstrip antenna.Table 1
Parameters of the transition structure of RF MEMS switch integrated in microstrip antenna.
ParametersS1 (mm)S2 (mm)L10.120.14L20.250.28W10.200.20W20.600.51W30.300.30Simulation results of the reflection coefficient of FRA integrated RF MEMS switches are shown in Figure6. Under different frequency reconstruction states, the impedance bandwidth and center frequency of the FRA are 110 MHz (8.7 GHz), 226 MHz (17.0 GHz), and 1902 MHz (31.1 GHz), respectively. The reflection coefficients of the antenna using the ideal switch and the antenna using the RF MEMS switch are evaluated and compared, and the basically matched frequency reconstruction characteristics are obtained, which also indicates that the effective integration of the switches is achieved through introducing the switch transition structure.Figure 6
Simulation results of the reflection coefficient of FRA integrated RF MEMS switches.


## 2.1. Basic Structure Design

It is well known that the operating frequency of the antenna depends on the equivalent electrical length of the radiator. Generally speaking, the longer the equivalent electrical length, the lower the operating frequency. Motivated by that, an easy way to achieve multiband reconfigurable antenna can start from the smallest size corresponding to the highest frequency, that is, by connecting additional patches with switches and by adjusting the overall size of the antenna by controlling the switches’ On and Off state. According to this principle, the basic structure of the proposed FRA element is shown in Figure1. Three multiscale microstrip patches are printed on the Rogers 4350B dielectric substrate, whose dielectric constant is 3.66, loss tangent is 0.004, and thickness is 0.508 mm. It is fed by using a coaxial line. When designing the basic structure of the FRA element, the two red rectangles of 2.0 mm × 1.1 mm in Figure 1 indicate that RF switches are replaced by copper plates to adjust the antenna topology. The connection or disconnection of the metal strip is equivalent to the On/Off function of the switch. When S1 is On and S2 is Off, the FRA element can work in X-band. When S1 is Off and S2 is On, the FRA element can work in Ku-band. Otherwise, when both S1 and S2 switches are Off, the FRA element will work in Ka-band. Figure 2 shows the optimized process of the size of the three radiators.Figure 1
Geometry of the proposed FRA element. (a) 3D view. (b) Front view (unit (mm):a = 17.0, b = 34.0, m1 = n1 = 2.3, m2 = 1.0, n2 = 5.0, m3 = n3 = 5.0, d = 0.4, p=1.0, L1 = 1.1, and L2 = 2.0).
(a)(b)Figure 2
Optimized results of the three radiators. (a) Ka-band. (b) Ku-band. (c) X-band.
(a)(b)(c)In addition, the antenna is utilized to construct a linear array working at the Ka-band (highest), which limits the size of the antenna element in the array dimension. The recent research shows that miniaturization of microstrip antennas can be achieved by shorting surfaces, shorting strips, or shorting probes [6, 20]. Inspired by that, five metal shorting holes between the microstrip patch and the ground plate are employed to reduce the overall antenna size in this paper, and through the optimization of the diameter and spacing of the metal shorting holes, a significant reduction in bandwidth is avoided, the optimized results of which are shown in Figure 2(c).Figure3 shows the simulation results of reflection coefficients at different frequency reconstruction states. It can be seen that FRA can work in X-band, Ku-band, and Ka-band. Taking the reflection coefficient less than −10 dB as the reference, the impedance bandwidth and center frequency are 106 MHz (8.6 GHz), 230 MHz (17.1 GHz), and 1900 MHz (31.1 GHz), respectively. Moreover, the reconstruction frequency ratio of the FRA reaches 3.61 : 1, and the size is 5.0 mm × 12.3 mm, which is only 0.143λX × 0.353λX, at the lowest frequency (8.6 GHz).Figure 3
Simulation results of reflection coefficients at different frequency reconstruction states.


## 2.2. FRA Integrated RF MEMS Switch Design

The coplanar waveguide capacitive MEMS switch proposed by the author’s research group is used. The substrate material is high-resistance silicon. The insulating layer is formed by thermal oxidation of a silicon substrate, whose main material component is silicon oxide. A detailed description of the switch can be found in [21].The structure of the FRA integrated RF MEMS switch is shown in Figure4. Based on the antenna structure in the ideal switching state, a prepreg layer for lamination is added under the ground plate, and a Rogers 4350B dielectric substrate with a thickness of 0.508 mm is introduced, which is used to route the coaxial feed port and the DC bias lines of the RF MEMS switches. Gold wire with 20 um diameter is used to bond RF MEMS switches and microstrip patches.Figure 4
Structure of the FRA integrated RF MEMS switches.The transition structure of the RF MEMS switch integrated into the microstrip antenna is shown in Figure5, and the transition structures of the switches S1 and S2 have different sizes as shown in Table 1. The CPW center signal line of the RF MEMS switch is connected to the microstrip antenna radiation patch through a piece of trapezoidal gradient impedance transformation structure to achieve impedance matching. In addition, a rectangular slot for switch installation is designed with a gap of Fc = 75 μm, an area of 1.35 mm × 1.25 mm (Wc × Lc), and a depth of 410 μm.Figure 5
Transition structure of RF MEMS switch integrated in microstrip antenna.Table 1
Parameters of the transition structure of RF MEMS switch integrated in microstrip antenna.
ParametersS1 (mm)S2 (mm)L10.120.14L20.250.28W10.200.20W20.600.51W30.300.30Simulation results of the reflection coefficient of FRA integrated RF MEMS switches are shown in Figure6. Under different frequency reconstruction states, the impedance bandwidth and center frequency of the FRA are 110 MHz (8.7 GHz), 226 MHz (17.0 GHz), and 1902 MHz (31.1 GHz), respectively. The reflection coefficients of the antenna using the ideal switch and the antenna using the RF MEMS switch are evaluated and compared, and the basically matched frequency reconstruction characteristics are obtained, which also indicates that the effective integration of the switches is achieved through introducing the switch transition structure.Figure 6
Simulation results of the reflection coefficient of FRA integrated RF MEMS switches.


## 3. Design of FRA Array

### 3.1. Spacing Optimization of FRA Element

As shown in Figure7, consider an N-element linear scan array distributed along the x-axis [22], let d be the distance between the array elements, and let θB be the scan angle; then the total field strength at the observation point P in the far field of the array can be expressed as(1)En=feθ∑n=1Nanej2π/λn−1dsinθ−sinθB,where feθ is the radiation pattern of a single antenna element, θ is the angle from boresight, λ is the wavelength, and an represents the amplitude weighting coefficient of each array element.Figure 7
Schematic diagram of linear array antenna.If the array is required not to generate grating lobes,d has to satisfy the following conditions:(2)d<λ1+sinθB.It can be known from (2) that if the frequency reconfigurable linear array is designed with the array element spacing in the Ka-band, the constraint conditions for the element interval without the grating lobe are satisfied in both X-band and Ku-band. However, for the X-band reconstruction state, since the antenna array units are too dense, an increase in coupling effects and a decrease in radiation efficiency and gain can be resulted. If the array spacing design is performed in the X-band, the sidelobe level of the Ka-band will inevitably be reduced, and even grating lobes can appear. Therefore, the optimization of the array element spacing becomes a key factor in the design of trifrequency FRAA.Genetic algorithm and full wave analysis software HFSS were jointly used to solve the optimization problem of reconfigurable antenna [23]. An improved fruit-fly optimization algorithm (FOA) is proposed to reduce the sidelobe level for antenna array synthesis in [24]. In this paper, the distances between FRA elements are taken as the optimization objectives, and the improved fruit-fly optimization algorithm and MATLAB-HFSS joint simulation are used to optimize the line irregular FRAA. The spacing optimization flowchart of the linear irregular FRAA elements is shown in Figure 8.Figure 8
Flowchart of spacing optimization of the linear irregular FRAA elements.


### 3.2. FRAA Design

Based on the FRA element designed previously and the array unit spacing optimization process shown in Figure9, a 1 × 16 linear irregular FRAA with beam deflection capability is designed. Then, the optimization objective is denoted as D=d1,d2,…di,…,d15, where di is the spacing between the i-th and the (i + 1)-th FRA element. The optimization interval of the element spacing is 6.5 mm to 20 mm. The optimization objective function of this FRAA is defined as follows:(3)minDmaxSLLX, Ku, KaD−SLLdgn,s.t.D=d1,d2,…di,…,d15,di∈6.5mm,20mm,where maxSLLX, Ku, KaD is the maximum sidelobe level of the array pattern at the three frequency bands and SLLdgn is the optimization constraint for the sidelobe level, which is −15 dB in the optimization.Figure 9
The schematic of the 1 × 16 linear irregular FRAA.In order to simplify the design optimization process of the 1 × 16 linear irregular array, copper microstrip lines are used instead of RF MEMS switches. The radiating surface structure is shown in Figure9. The 16 red rectangles and 16 blue rectangles, respectively, represent a switch group K1 and a switch group K2 composed of copper strips. The optimized element spacing and the required phases are provided in Figure 10. The length of the effective radiation aperture of the FRAA is 128.0 mm.Figure 10
Optimization results of FRAA element spacing and port feed phases.When K1 is On and K2 is Off, the FRAA works in X-band. When K1 is Off and K2 is On, the FRAA can work in Ku-band. In addition, when both K1 and K2 are Off, the FRAA will work in Ka-band. From the results of the reflection coefficients of different frequency reconstruction states in Figure11, it can be seen that the impedance bandwidth and center frequency of the FRAA are 110.0 MHz (8.7 GHz), 195.0 MHz (17.1 GHz), and 1800 MHz (30.0 GHz), respectively. Moreover, the reconstruction frequency ratio of the FRA reaches 3.45 : 1. The frequency reconstruction capability of the antenna array and the frequency reconfigurable antenna unit is basically the same.Figure 11
Simulation results of the reflection coefficient of FRAA.Simulation results of the radiation pattern of the FRAA under constant amplitude feeding conditions are shown in Figure12. Corresponding to the reconstruction states of Ka-band, Ku-band, and X-band, the main polarization states are all vertical polarization, and the cross-polarization levels are −15.8 dB, −23.3 dB, and −17.5 dB, respectively. Besides, the sidelobe levels are −15.7 dB, −17.0 dB, and −16.2 dB, respectively. The FRAA gains are 18.1 dB, 17.0 dB, and 12.5 dB. In addition, the pattern beams deflection of the three states is the same; that is, θxoz=20°.Figure 12
Simulated radiation pattern of the linear irregular FRAA with the beam steering angles ofθxoz=20°.For fair comparison, a conventional uniform-pitch phased array is designed under the condition that the effective radiation aperture of the antenna array is 128 mm with uniform amplitude excitation. The radiating surface structure of the uniform FRAA is shown in Figure13. The states of the switch groups corresponding to different frequency reconstructions are the same as those of the irregular array shown in Figure 9. However, all the spacing between the array elements is 8.2 mm.Figure 13
The schematic of the 1 × 16 linear uniform FRAA.Figure14 shows the radiation pattern of the uniform array. Due to the effect of the array factor, the beam deflection is still θxoz=20°. Moreover, since the array aperture and the number of array elements are not changed, its antenna gains and 3 dB beam width are almost the same as those of the irregular FRAA. However, it can also be seen that the sidelobe levels are −12.7 dB, −12.5 dB, and −12.3 dB in Ka-band, Ku-band, and X-band, respectively. The increase in the sidelobe levels of the uniform array relative to the irregular FRAA is more than 3 dB, as shown in Figure 15. It should be noted that when the uniform FRAA works in the Ka-band state, an obvious grating lobe appears at −53° in the pattern, which mainly because the array element spacing exceeds the limit condition of (2). When the array works in the Ka-band and the scanning angle is 20°, the interval between the arrays should be controlled within 7.2 mm to avoid the generation of grating lobes. However, under this constraint, the array element spacing in the X-band operating state is less than 0.2λX, which can definitely result in the strong coupling effect between array elements.Figure 14
Simulated radiation pattern of the uniform FRAA with the beam steering angles ofθxoz=20°.Figure 15
Comparison of sidelobe levels in irregular and uniform FRAA.To show the superiority, the irregular FRAA proposed in this paper is compared with other counterparts as listed in Table2. The tunable FRA element has advantages in the frequency reconstruction range and the number of switches used. In addition, the irregular FRAA optimized by the joint intelligent algorithm and MATLAB-HFSS also achieves a relatively low sidelobe level with uniform amplitude feeding. It can also be seen that the proposed FRA element structure has good potential in forming an array, and the implementation of the FRAA has the capability to solve the problem of the constraint of the element spacing in the current FRAA design.Table 2
Comparison of the FRAA with other multiband/switchable-band antenna arrays.
ItemOur workRef. [14]Ref. [16]Ref. [19]Ref. [18]Reconstruction bandX/Ku/KaX/Ku/KaL/SL/CX/Ku (multiband)Frequency ratio3.57 : 13.12 : 12.2 : 13.2 : 11.8 : 1Number of element switches244160Scanning range20°0°±60°±60°50°Is the amplitude weightedNoNoNoNot mentionedNoSidelobe level simulation result (dB)−15.7@20°Not mentionedAround −12.5@15°Around −12.0@0°−14.0 (synthetic)Element size (λL)0.14 × 0.350.14 × 0.130.22 × 0.220.18 × 0.180.33 × 0.33Element spacing (λL/λH)Irregular0.4/1.270.5/0.50.36/<0.50.33/0.58


## 3.1. Spacing Optimization of FRA Element

As shown in Figure7, consider an N-element linear scan array distributed along the x-axis [22], let d be the distance between the array elements, and let θB be the scan angle; then the total field strength at the observation point P in the far field of the array can be expressed as(1)En=feθ∑n=1Nanej2π/λn−1dsinθ−sinθB,where feθ is the radiation pattern of a single antenna element, θ is the angle from boresight, λ is the wavelength, and an represents the amplitude weighting coefficient of each array element.Figure 7
Schematic diagram of linear array antenna.If the array is required not to generate grating lobes,d has to satisfy the following conditions:(2)d<λ1+sinθB.It can be known from (2) that if the frequency reconfigurable linear array is designed with the array element spacing in the Ka-band, the constraint conditions for the element interval without the grating lobe are satisfied in both X-band and Ku-band. However, for the X-band reconstruction state, since the antenna array units are too dense, an increase in coupling effects and a decrease in radiation efficiency and gain can be resulted. If the array spacing design is performed in the X-band, the sidelobe level of the Ka-band will inevitably be reduced, and even grating lobes can appear. Therefore, the optimization of the array element spacing becomes a key factor in the design of trifrequency FRAA.Genetic algorithm and full wave analysis software HFSS were jointly used to solve the optimization problem of reconfigurable antenna [23]. An improved fruit-fly optimization algorithm (FOA) is proposed to reduce the sidelobe level for antenna array synthesis in [24]. In this paper, the distances between FRA elements are taken as the optimization objectives, and the improved fruit-fly optimization algorithm and MATLAB-HFSS joint simulation are used to optimize the line irregular FRAA. The spacing optimization flowchart of the linear irregular FRAA elements is shown in Figure 8.Figure 8
Flowchart of spacing optimization of the linear irregular FRAA elements.


## 3.2. FRAA Design

Based on the FRA element designed previously and the array unit spacing optimization process shown in Figure9, a 1 × 16 linear irregular FRAA with beam deflection capability is designed. Then, the optimization objective is denoted as D=d1,d2,…di,…,d15, where di is the spacing between the i-th and the (i + 1)-th FRA element. The optimization interval of the element spacing is 6.5 mm to 20 mm. The optimization objective function of this FRAA is defined as follows:(3)minDmaxSLLX, Ku, KaD−SLLdgn,s.t.D=d1,d2,…di,…,d15,di∈6.5mm,20mm,where maxSLLX, Ku, KaD is the maximum sidelobe level of the array pattern at the three frequency bands and SLLdgn is the optimization constraint for the sidelobe level, which is −15 dB in the optimization.Figure 9
The schematic of the 1 × 16 linear irregular FRAA.In order to simplify the design optimization process of the 1 × 16 linear irregular array, copper microstrip lines are used instead of RF MEMS switches. The radiating surface structure is shown in Figure9. The 16 red rectangles and 16 blue rectangles, respectively, represent a switch group K1 and a switch group K2 composed of copper strips. The optimized element spacing and the required phases are provided in Figure 10. The length of the effective radiation aperture of the FRAA is 128.0 mm.Figure 10
Optimization results of FRAA element spacing and port feed phases.When K1 is On and K2 is Off, the FRAA works in X-band. When K1 is Off and K2 is On, the FRAA can work in Ku-band. In addition, when both K1 and K2 are Off, the FRAA will work in Ka-band. From the results of the reflection coefficients of different frequency reconstruction states in Figure11, it can be seen that the impedance bandwidth and center frequency of the FRAA are 110.0 MHz (8.7 GHz), 195.0 MHz (17.1 GHz), and 1800 MHz (30.0 GHz), respectively. Moreover, the reconstruction frequency ratio of the FRA reaches 3.45 : 1. The frequency reconstruction capability of the antenna array and the frequency reconfigurable antenna unit is basically the same.Figure 11
Simulation results of the reflection coefficient of FRAA.Simulation results of the radiation pattern of the FRAA under constant amplitude feeding conditions are shown in Figure12. Corresponding to the reconstruction states of Ka-band, Ku-band, and X-band, the main polarization states are all vertical polarization, and the cross-polarization levels are −15.8 dB, −23.3 dB, and −17.5 dB, respectively. Besides, the sidelobe levels are −15.7 dB, −17.0 dB, and −16.2 dB, respectively. The FRAA gains are 18.1 dB, 17.0 dB, and 12.5 dB. In addition, the pattern beams deflection of the three states is the same; that is, θxoz=20°.Figure 12
Simulated radiation pattern of the linear irregular FRAA with the beam steering angles ofθxoz=20°.For fair comparison, a conventional uniform-pitch phased array is designed under the condition that the effective radiation aperture of the antenna array is 128 mm with uniform amplitude excitation. The radiating surface structure of the uniform FRAA is shown in Figure13. The states of the switch groups corresponding to different frequency reconstructions are the same as those of the irregular array shown in Figure 9. However, all the spacing between the array elements is 8.2 mm.Figure 13
The schematic of the 1 × 16 linear uniform FRAA.Figure14 shows the radiation pattern of the uniform array. Due to the effect of the array factor, the beam deflection is still θxoz=20°. Moreover, since the array aperture and the number of array elements are not changed, its antenna gains and 3 dB beam width are almost the same as those of the irregular FRAA. However, it can also be seen that the sidelobe levels are −12.7 dB, −12.5 dB, and −12.3 dB in Ka-band, Ku-band, and X-band, respectively. The increase in the sidelobe levels of the uniform array relative to the irregular FRAA is more than 3 dB, as shown in Figure 15. It should be noted that when the uniform FRAA works in the Ka-band state, an obvious grating lobe appears at −53° in the pattern, which mainly because the array element spacing exceeds the limit condition of (2). When the array works in the Ka-band and the scanning angle is 20°, the interval between the arrays should be controlled within 7.2 mm to avoid the generation of grating lobes. However, under this constraint, the array element spacing in the X-band operating state is less than 0.2λX, which can definitely result in the strong coupling effect between array elements.Figure 14
Simulated radiation pattern of the uniform FRAA with the beam steering angles ofθxoz=20°.Figure 15
Comparison of sidelobe levels in irregular and uniform FRAA.To show the superiority, the irregular FRAA proposed in this paper is compared with other counterparts as listed in Table2. The tunable FRA element has advantages in the frequency reconstruction range and the number of switches used. In addition, the irregular FRAA optimized by the joint intelligent algorithm and MATLAB-HFSS also achieves a relatively low sidelobe level with uniform amplitude feeding. It can also be seen that the proposed FRA element structure has good potential in forming an array, and the implementation of the FRAA has the capability to solve the problem of the constraint of the element spacing in the current FRAA design.Table 2
Comparison of the FRAA with other multiband/switchable-band antenna arrays.
ItemOur workRef. [14]Ref. [16]Ref. [19]Ref. [18]Reconstruction bandX/Ku/KaX/Ku/KaL/SL/CX/Ku (multiband)Frequency ratio3.57 : 13.12 : 12.2 : 13.2 : 11.8 : 1Number of element switches244160Scanning range20°0°±60°±60°50°Is the amplitude weightedNoNoNoNot mentionedNoSidelobe level simulation result (dB)−15.7@20°Not mentionedAround −12.5@15°Around −12.0@0°−14.0 (synthetic)Element size (λL)0.14 × 0.350.14 × 0.130.22 × 0.220.18 × 0.180.33 × 0.33Element spacing (λL/λH)Irregular0.4/1.270.5/0.50.36/<0.50.33/0.58


## 4. Fabrication and Measurement

Based on the design of the FRA element in Section2, three prototypes with ideal switch of the FRA element processed are shown in Figure 16. The feed port is equipped with a 2.92-KFD0705 RF connector that can support frequencies up to 40 GHz, covering the whole frequency reconfigurable range. To test the reflection coefficient of the antenna, Agilent A5244A vector network analyser, with a maximum adaptive frequency of 50 GHz, is used. The reflection coefficient test results of the FRA unit are shown in Figure 17. The results of the prototype test and theoretical simulation are in good agreement. The center frequency and impedance bandwidth of different frequency reconstruction states are almost unchanged compared with the simulation results, which proves that the FRA unit proposed in this paper has good frequency reconstruction characteristics.Figure 16
The fabricated FRA prototypes.Figure 17
Measured reflection coefficients of FRA prototype working at different states.According to the FRAA design in Section3, three types of ideal switch FRAA prototypes are processed, and a uniform amplitude feeding network is added to each prototype. By simultaneously optimizing the feed line width of power divider and the length of the delay line, the amplitude consistency of each output port is achieved. Moreover, the feed phase difference of the FRAA prototype for each frequency reconstruction state is determined by Figure 10. The structure of the FRAA prototype is shown in Figure 18, and the processed FRAA prototypes are shown in Figure 19.Figure 18
Structure of the FRAA prototype with uniform amplitude feeding network.Figure 19
The fabricated 1 × 16 linear irregular FRAA prototype. (a) Radiation surface. (b) Feeding network surface.
(a)(b)The radiation patterns of FRAA prototypes are tested in a microwave shielded room, as shown in Figure20. Figure 21 shows the simulated and measured results of the FRAA normalized radiation pattern under uniform feeding conditions. The sidelobe level simulation results of FRAA operating in X-band, Ku-band, and Ka-band are −15.1 dB, −14.9 dB, and −14.3 dB, respectively. The results of the sidelobe level measurements are −13.6 dB, −13.1 dB, and −12.1 dB, respectively. Due to the testing environment error, the sidelobe level is slightly increased, which shows that the sidelobe level increases with the increase of the operating frequency. On the whole, the simulated and measured results are in good agreement.Figure 20
The measured scene.Figure 21
The normalized radiation pattern measured and simulated results of FRAA prototypes in different frequency reconstruction states. (a) X-band. (b) Ku-band. (c) Ka-band.
(a)(b)(c)


## 5. Conclusion

In this paper, a frequency reconfigurable antenna element integrating two RF MEMS switches has been proposed. The FRA element has the reconstruction capability in X-band, Ku-band, and Ka-band, and the frequency reconstruction ratio reaches 3.57 : 1. Besides, the miniaturization design of the element has been achieved through five metal shorting holes between the radiating surface and the ground plate, reaching 0.14λX × 0.35λX, providing a good structural basis for the frequency reconfigurable antenna array. By employing intelligent algorithm and MATLAB-HFSS joint optimization, a 1 × 16 linear irregular FRAA based on the FRA element has been proposed, which realizes that beam deflection in the same direction corresponds to different frequency reconstruction state. In addition, compared with the traditional uniformly spaced FRAA, the sidelobe level of the irregular antenna line array is improved by not less than 3 dB, and the grating lobe in the Ka band is effectively avoided. Finally, both FRA element and FRAA prototypes have been fabricated and tested to verify their superiority. The measurement results show that the proposed trifrequency reconfigurable linear irregular FRAA has broad application prospects in the future multifrequency wireless communication and intelligent radar anti-interference fields.



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*Source: 9074135-2020-06-24.xml*