# Polarization and DOA Estimation Based on Dual-Polarized Conformal Array

Authors: Chao Liu; Shuai Xiang; Liangfeng Xu; Zhengfei Fang
Journal: International Journal of Antennas and Propagation
 (2019)

---

## Abstract

A dual-polarized multiple signal classification (DP-MUSIC) algorithm is presented to estimate the arrival directions and polarizations for a dual-polarized conformal array. Each polarization signal is decomposed into two orthogonal polarization components, which are considered to be a pair of coherent signals coming from the same direction but different polarization. The polarization parameters are modeled as the equivalent coherence coefficients of the orthogonal polarization components. Then, the method of decoherence can be used to decouple the information of polarization states and signal angles. After that, the direction of arrival (DOA) and polarization parameters can be estimated by the DP-MUSIC algorithm. Moreover, the angles of incident direction are re-estimated, which greatly improves the accuracy of DOA estimation. The Cramer–Rao bound (CRB) is derived and the effectiveness of the proposed algorithm is verified by Monte Carlo simulations.


---

## Body

## 1. Introduction

Conformal array is an antenna array that conforms to the surface of the carrier. Conformal antennas have been widely applied in the area of radar, navigation, radio communications, and satellite applications with their special advantages [1]. Super-resolution direction finding is one of the most important research directions. However, due to the inconsistency of the polarization characteristics of the conformal array, the information of polarization and direction of arrival (DOA) are coupled with each other, which brings new problems to the estimation of the parameters.The multiple signal classification (MUSIC) algorithm was proposed by Schmidt to estimate the DOA of the signal in [2]. In [3], the MUSIC-based DOA estimation algorithm incorporating the oblique projection was proposed. In [4], a method for estimating the arrival direction of array interpolation based on compressed sensing was proposed. However, these algorithms leave out of consideration the effects of polarization of antenna elements.Polarization is a problem that cannot be ignored. Therefore, the polarization sensitivity of array to incident signals needs to be considered in DOA estimation. In [5], the estimation of signal parameters via rotational invariance techniques (ESPRIT) was proposed to estimate the DOA and polarization parameters of incoming plane waves with a uniform linear array. In [6, 7], the polarization smoothing algorithm (PSA) was proposed to estimate arrival directions and polarizations for a coherent source. This method requires the steering vector of the array to be written as the Kronecker product of the spatial steering vector and the polarized vector. Actually, only planar array can satisfy this relationship, and conformal array does not have these characteristics because of the inconsistency of the polarization of the elements.In [8], a blind polarization DOA estimation method was proposed by using three pairs of special subarrays for conical conformal array. In [9], based on the fourth-order cumulant of array measurements and special array design structure, a blind DOA estimation algorithm was proposed for the conformal array. However, they require that the conformal array contains linear subarrays. Therefore, these methods are not applicable to the arbitrary conformal array structure. The aforementioned works for directions and polarizations are studied based on the single-polarized array. In [10, 11], the performance of the single-polarized and dual-polarized antenna array was analyzed and compared. It is possible to conclude that the performance of a dual-polarized antenna array is significantly better than that of a single-polarized array. In [12], DOA and polarization estimation for unequal power sources was proposed based on reconstructed noise subspace. However, this method is not suitable for conformal arrays. In [13], a blind polarization DOA estimation method was proposed based on the dual feed conformal array for polarization diversity signals. But this method is only applicable to orthogonal polarization signals and does not involve DOA estimation of general polarization signals.In this paper, a dual-polarized multiple signal classification (DP-MUSIC) method is presented based on the dual-polarized conformal array. Each polarization signal is decomposed into two orthogonal polarization components, which are considered to be a pair of coherent signals. The polarization parameters are modeled as the coherence coefficients of each pair of polarization components. And then, decoupling of polarization and DOA can be converted to the decoherence problem. Since the conventional decoherence technique cannot be applied to the conformal array, it is firstly projected onto a uniform planar array. And then, the forward-backward smoothing technique is adopted to solve the coherence problem. After that, the DOA and polarization parameters can be estimated. DP-MUSIC-based spectrum is constructed for the DOA estimation. And the corresponding polarization parameters can be estimated by using the estimated DOA. Additionally, DOA is re-estimated by using the original received data and the estimated polarization parameters to further improve the DOA estimation accuracy. The Cramer–Rao bound (CRB) is derived to verify the performance of the algorithm. Finally, the validity of the proposed algorithm is demonstrated by simulation experiments.


## 2. Signal Model

Consider an ideal dual-polarized conformal array withN elements shown in Figure 1. The coupling between antenna elements and polarization components is not considered, and the two feed points of the dual-polarized antenna excite and receive their polarization components independently [14]. Ox,y,z is the global coordinate system of the conformal array, and Oi′x′,y′,z′ is the local coordinate system of the ith array element. θ and ϕ represent the elevation and azimuth of the incident signal, respectively. θi′ and ϕi′ are the associated elevation and azimuth in the ith local coordinate system.Figure 1
Conformal array coordinate diagram.Assume that the two feed points of the antenna receive the signals ofθ-polarization and the ϕ-polarization component, respectively. In order to conveniently synthesis the far field pattern of the conformal array, the components of all the elements need to be unified into the same coordinate system to count their contributions to the whole conformal array radiation. The mapping angle θi′,ϕi′ of the direction θ,ϕ in the ith local coordinate system can be calculated by the following formula:(1)sinθi′cosϕi′sinθi′sinϕi′cosθi′=Rglisinθcosϕsinθsinϕcosθ,where Rgli signifies the Euler rotation matrix from global to local of ith element [15, 16]. In order to calculate the mapping component of the signal in the local coordinate system conveniently, it is transformed into a Cartesian coordinate system.(2)sxt=−sθtcosθcosϕ−sϕtsinϕ,syt=−sθtcosθsinϕ+sϕtcosϕ,szt=sθtsinθ.Define the transform matrixTscθ,ϕ from spherical coordinates to Cartesian coordinates in the direction θ,ϕ.(3)Tscθ,ϕ=−cosθcosϕ−sinϕ−cosθsinϕcosϕsinθ0.Equation (2) can be expressed as(4)sxtsytszt=Tscθ,ϕsθtsϕt.The mapping components of the signal in the local coordinate system can be expressed as(5)sx′tsy′tsz′t=Rglisxtsytszt,siθ′tsiϕ′t=Tcsiθi′,ϕi′sx′tsy′tsz′t,where Tcsiθi′,ϕi′ represents the transform matrix of the ith element from Cartesian coordinates to spherical coordinates in the direction θi′,ϕi′.(6)Tcsiθi′,ϕi′=00−1sinθi′−sinϕi′cosϕi′0.Then, the electric field components of the signal in theθ and ϕ directions of the ith element can be expressed as(7)siθ′tsiϕ′t=Tcsiθi′,ϕi′RgliTscθ,ϕsθtsϕt.Define the transformation matrix of theith array element Tiθ,ϕ=Tcsiθi′,ϕi′RgliTscθ,ϕ. The mapped components of the signal on the whole array can be expressed as(8)s1θ′ts1ϕ′t⋮sNθ′tsNϕ′t=T1θ,ϕ⋮TNθ,ϕsθtsϕt.Without considering the noise, the received data of array can be expressed as(9)x1θ′tx1ϕ′t⋮xNθ′txNϕ′t=g1θ′θ1′,ϕ1′a1θ,ϕs1θ′tg1ϕ′θ1′,ϕ1′a1θ,ϕs1ϕ′t⋮gNθ′θN′,ϕN′aNθ,ϕsNθ′tgNϕ′θN′,ϕN′aNθ,ϕsNϕ′t,where giθ′θ′,ϕ′ and giϕ′θ′,ϕ′ are θ-polarized and ϕ-polarized components of the ith antenna element pattern in the local coordinate system, respectively.(10)aθ,ϕ=e−jkr1v,⋯,e−jkrNvT,where ri=xi,yi,zi, i=1,2,⋯,N is the position vector of ith array element in the global coordinate system. v=sinθcosϕ,sinθsinϕ,cosθT is the unit direction vector of θ,ϕ. k=2π/λ is the wavenumber, where λ is the wavelength of the incoming signals. The symbol “·T” means the transpose of matrix. Define(11)Gθ,ϕ=diagg1θ′θ1′,ϕ1′,g1ϕ′θ1′,ϕ1′,⋯,gNθ′θN′,ϕN′,gNϕ′θN′,ϕN′,Tθ,ϕ=T1θ,ϕ0⋯00T2θ,ϕ⋯0⋮⋮⋱⋮00⋯TNθ,ϕ.Equation (9) can be expressed as(12)xt=Gθ,ϕTθ,ϕaθ,ϕ⊗I2sθtsϕt,where I2 is the 2×2 identity matrix.(13)a˜θ,ϕ=Gθ,ϕTθ,ϕaθ,ϕ⊗I2=a˜θθ,ϕ,a˜ϕθ,ϕ,where a˜θθ,ϕ and a˜ϕθ,ϕ represent the 2N×1 equivalent steering vector for the θ-polarized and ϕ-polarized components coming from the direction θ,ϕ, respectively. The symbol “⊗” means the Kronecker product.Although the previous derivation is based on the linear polarization model, the model can also be applied to a conformal array of arbitrary dual-polarized antennas. The steering vector of arbitrary dual-polarized conformal array can be written as(14)a˜θ,ϕ=Gθ,ϕTθ,ϕaθ,ϕ⊗L−T,where L is a linear transformation matrix between different polarizations. For the dual-polarized antennas consisting of circular polarization, the linear transformation matrix is(15)L=12−j212j2.If one dual-polarized component-antenna consists of anθ-polarized antenna, whereas another dual-polarized component-antenna consists of a right-hand circular antenna, the linear transformation matrix is(16)L=1012j2.Without loss of generality, the conformal array model ofθ-polarization and ϕ-polarization is adopted in the following derivation and analysis.Consider an incident signalst with arbitrary polarization, and it is decomposed into two orthogonal polarization signals as sθt=sinγejηst and sϕt=cosγst, respectively. Suppose that there are K narrow-band independent sources in the far field, and the received data of array can be expressed as(17)xt=∑i=1Ka˜θθi,ϕisiθt+∑i=1Ka˜ϕθi,ϕisiϕt+nt=∑i=1K​a˜θθi,ϕisinγiejηi+a˜ϕθi,ϕicosγisit+nt.Define the block diagonal matrix consisting of polarization parameters as(18)Pγ,η=pγ1,η1⋯0⋮⋱⋮0⋯pγK,ηK,(19)pγi,ηi=sinγiejηi,cosγiT,i=1,⋯,K,where γi and ηi are the polarization parameters of the ith incoming signal. γ∈0,π/2 and η∈−π,π are defined to characterize the respective amplitude ratio and the phase difference between the two polarization components, respectively.Combining formulas (17)–(19), the following equation can be derived(20)xt=a˜θθ1,ϕ1,a˜ϕθ1,ϕ1,⋯,a˜θθK,ϕK,a˜ϕθK,ϕKpγ1,η1⋯0⋮⋱⋮0⋯pγK,ηK·s1t⋮sKt+nt.The equivalent array manifold of the dual-polarized conformal array is a matrix of2N×2K, and it can be written as(21)A˜=a˜θθ1,ϕ1,a˜ϕθ1,ϕ1,⋯,a˜θθK,ϕK,a˜ϕθK,ϕK.Finally, the received data of array can be written as(22)xt=A˜Pst+nt,(23)st=s1t,⋯,sKtT,(24)nt=n1θt,n1ϕt,⋯,nNθt,nNϕtT,where st denotes the K×1 vectors of the incident signals, and nt denotes the 2N×1 Gaussian white noise with zero mean and variance σn2. From equation (22), it can be found that all the information of polarization is contained in the matrix P, which can be seen as the coherence coefficient matrix in this model.


## 3. Polarization and DOA Estimation

In Section2, each polarization signal is decomposed into two orthogonal polarization components, which are considered to be coherent signals coming from the same direction but different polarization. The polarization parameters are modeled as coherence coefficients of each pair of polarization components. And in this section, the decoherence of conformal array is achieved by using the virtual projection transformation and spatial smoothing technique. The DP-MUSIC algorithm is used to estimate the DOA of dual-polarized conformal array.


### 3.1. Virtual Projection Transformation

Assume that the observation areas of elevation and azimuth angles of the virtual transformation areΘ=θl,θr and Φ=ϕl,ϕr, respectively. The areas are evenly divided by intervals Δθ and Δϕ. In that way, the original array manifold matrix and the virtual array manifold matrix of the dual-polarized uniform planar array can be written as [17](25)A˜r=a˜θθl,ϕl,a˜ϕθl,ϕl,a˜θθl+Δθ,ϕl,⋯,a˜ϕθr,ϕr−Δϕ,a˜θθr,ϕr,a˜ϕθr,ϕr,Av=apθl,ϕl,apθl+Δθ,ϕl,⋯,apθr,ϕr−Δϕ,apθr,ϕr⊗I2,where apθ,ϕ is the steering vector of the single-polarized uniform planar array. The approximate transformation can be realized by the virtual transformation relationship between the original array and the virtual array.(26)Av=BHA˜r,where the symbol “·H” denotes the conjugate transpose of the matrix and B is the 2N×2N transformation array, which can be solved by least squares.(27)B=A˜rA˜rH−1A˜rAvH.The covariance matrix of signal-received data can be written as(28)Rx=ExtxHt=A˜RsA˜H+σn2I,where Rs=PR˜sPH. R˜s is the covariance matrix of signal source, σn2 is the noise power, and I is a 2N×2N identity matrix. Then, the covariance matrix of the virtual array can be expressed as follows [18]:(29)R¯x=BHRxB=BHA˜RsBHA˜H+σn2BHB.Generally,BHB≠I. Therefore, the white noise of the original array becomes colored noise by the virtual transformation. In order to turn colored noise into white noise, the transformation array B by prewhitening processing can be changed to(30)B¯=BHB−1/2BH.Consequently, the covariance matrix of the virtual transformation array after noise prewhitening processing is(31)R¯x=B¯RxB¯H.As can be seen from the model in equation (22), there are two coherent signals in each group. The spatial forward-backward smoothing process is used to realize decoherence. The covariance matrix can be expressed as(32)R¯xfb=R¯x+JR¯x∗J2,where J is the 2N×2N inverse identity matrix, and the symbol “·∗” denotes complex conjugate of matrix.


### 3.2. Parameter Estimation

After the above processing, the depolarization and decoherence are realized. In this paper, the DP-MUSIC algorithm is used to estimate the azimuth and elevation of signals.The eigenvalue decomposition (EVD) ofR¯xfb(33)R¯xfb=U¯sΛ¯sU¯s+U¯nΛ¯nU¯n,where U¯s∈ℂ2N×2K and U¯n∈ℂ2N×2N−2K are the signal and noise subspaces spanned by eigenvectors corresponding to the eigenvalues Λ¯s and Λ¯n, respectively.The steering vector of the virtual projection isB¯a˜θ,ϕ. Define(34)Qθ,ϕ=a˜Hθ,ϕB¯HU¯nU¯nHB¯a˜θ,ϕ=a˜θθ,ϕ,a˜ϕθ,ϕHB¯HU¯nU¯nHB¯a˜θθ,ϕ,a˜ϕθ,ϕ,where Qθ,ϕ is a 2×2 matrix. The arbitrary polarization signal has at least one component in the polarization space. Then when θ,ϕ is equal to the actual arrival directions θi,ϕi, i=1,⋯,K, the diagonal elements in the Qθ,ϕ has at least one element that is zero. B¯HU¯nU¯nHB¯ is a positive semidefinite matrix, so the following pseudospectral can be constructed to estimate the angles of the signals:(35)Pθ,ϕ=1min1≤i≤2Qiiθ,ϕ.The DOAs are estimated by searching theK highest peaks of the pseudospectrum, denoted as θ^i,ϕ^i.After DOA estimated values are obtained, the polarization parameters are estimated by using DOA estimation values and original received data.Us and Un are the signal and noise subspaces of Rx. The DOA estimation value for each group corresponds to the estimates of one group of polarization parameters. Plugging the estimated values θ^i,ϕ^i into formula (22), and the polarized steering vector can be expressed as(36)aθ^,ϕ^,γ,η=a˜θ^,ϕ^pγ,η.Each set of polarization parameters matches the corresponding angle-estimated value. The estimation values of the polarization parameters can be obtained from the following formula:(37)γ^i,η^i=argmaxγ,η1aHθ^i,ϕ^i,γ,ηUnUnHaθ^i,ϕ^i,γ,η,where i=1,⋯,K. The DOA is estimated on the basis of the virtual projection, which will lead to a transformation error. In order to reduce the error of the DOA estimation caused by the virtual projection transformation, the DOAs are re-estimated after obtaining the estimation values of the polarization parameters.The estimated valuesγ^i,η^i take the place of polarization parameters γ,η in formula (22), and the polarized steering vector can be rewritten as(38)aθ,ϕ,γ^,η^=a˜θ,ϕpγ^,η^.The pseudospectral expression of DOAs refined estimation is shown as(39)Pθ,ϕ=∑i=1K​1aHθ,ϕ,γ^i,η^iUnUnHaθ,ϕ,γ^i,η^i.From formula (39), the further refined estimation of DOAs can be obtained.


## 3.1. Virtual Projection Transformation

Assume that the observation areas of elevation and azimuth angles of the virtual transformation areΘ=θl,θr and Φ=ϕl,ϕr, respectively. The areas are evenly divided by intervals Δθ and Δϕ. In that way, the original array manifold matrix and the virtual array manifold matrix of the dual-polarized uniform planar array can be written as [17](25)A˜r=a˜θθl,ϕl,a˜ϕθl,ϕl,a˜θθl+Δθ,ϕl,⋯,a˜ϕθr,ϕr−Δϕ,a˜θθr,ϕr,a˜ϕθr,ϕr,Av=apθl,ϕl,apθl+Δθ,ϕl,⋯,apθr,ϕr−Δϕ,apθr,ϕr⊗I2,where apθ,ϕ is the steering vector of the single-polarized uniform planar array. The approximate transformation can be realized by the virtual transformation relationship between the original array and the virtual array.(26)Av=BHA˜r,where the symbol “·H” denotes the conjugate transpose of the matrix and B is the 2N×2N transformation array, which can be solved by least squares.(27)B=A˜rA˜rH−1A˜rAvH.The covariance matrix of signal-received data can be written as(28)Rx=ExtxHt=A˜RsA˜H+σn2I,where Rs=PR˜sPH. R˜s is the covariance matrix of signal source, σn2 is the noise power, and I is a 2N×2N identity matrix. Then, the covariance matrix of the virtual array can be expressed as follows [18]:(29)R¯x=BHRxB=BHA˜RsBHA˜H+σn2BHB.Generally,BHB≠I. Therefore, the white noise of the original array becomes colored noise by the virtual transformation. In order to turn colored noise into white noise, the transformation array B by prewhitening processing can be changed to(30)B¯=BHB−1/2BH.Consequently, the covariance matrix of the virtual transformation array after noise prewhitening processing is(31)R¯x=B¯RxB¯H.As can be seen from the model in equation (22), there are two coherent signals in each group. The spatial forward-backward smoothing process is used to realize decoherence. The covariance matrix can be expressed as(32)R¯xfb=R¯x+JR¯x∗J2,where J is the 2N×2N inverse identity matrix, and the symbol “·∗” denotes complex conjugate of matrix.


## 3.2. Parameter Estimation

After the above processing, the depolarization and decoherence are realized. In this paper, the DP-MUSIC algorithm is used to estimate the azimuth and elevation of signals.The eigenvalue decomposition (EVD) ofR¯xfb(33)R¯xfb=U¯sΛ¯sU¯s+U¯nΛ¯nU¯n,where U¯s∈ℂ2N×2K and U¯n∈ℂ2N×2N−2K are the signal and noise subspaces spanned by eigenvectors corresponding to the eigenvalues Λ¯s and Λ¯n, respectively.The steering vector of the virtual projection isB¯a˜θ,ϕ. Define(34)Qθ,ϕ=a˜Hθ,ϕB¯HU¯nU¯nHB¯a˜θ,ϕ=a˜θθ,ϕ,a˜ϕθ,ϕHB¯HU¯nU¯nHB¯a˜θθ,ϕ,a˜ϕθ,ϕ,where Qθ,ϕ is a 2×2 matrix. The arbitrary polarization signal has at least one component in the polarization space. Then when θ,ϕ is equal to the actual arrival directions θi,ϕi, i=1,⋯,K, the diagonal elements in the Qθ,ϕ has at least one element that is zero. B¯HU¯nU¯nHB¯ is a positive semidefinite matrix, so the following pseudospectral can be constructed to estimate the angles of the signals:(35)Pθ,ϕ=1min1≤i≤2Qiiθ,ϕ.The DOAs are estimated by searching theK highest peaks of the pseudospectrum, denoted as θ^i,ϕ^i.After DOA estimated values are obtained, the polarization parameters are estimated by using DOA estimation values and original received data.Us and Un are the signal and noise subspaces of Rx. The DOA estimation value for each group corresponds to the estimates of one group of polarization parameters. Plugging the estimated values θ^i,ϕ^i into formula (22), and the polarized steering vector can be expressed as(36)aθ^,ϕ^,γ,η=a˜θ^,ϕ^pγ,η.Each set of polarization parameters matches the corresponding angle-estimated value. The estimation values of the polarization parameters can be obtained from the following formula:(37)γ^i,η^i=argmaxγ,η1aHθ^i,ϕ^i,γ,ηUnUnHaθ^i,ϕ^i,γ,η,where i=1,⋯,K. The DOA is estimated on the basis of the virtual projection, which will lead to a transformation error. In order to reduce the error of the DOA estimation caused by the virtual projection transformation, the DOAs are re-estimated after obtaining the estimation values of the polarization parameters.The estimated valuesγ^i,η^i take the place of polarization parameters γ,η in formula (22), and the polarized steering vector can be rewritten as(38)aθ,ϕ,γ^,η^=a˜θ,ϕpγ^,η^.The pseudospectral expression of DOAs refined estimation is shown as(39)Pθ,ϕ=∑i=1K​1aHθ,ϕ,γ^i,η^iUnUnHaθ,ϕ,γ^i,η^i.From formula (39), the further refined estimation of DOAs can be obtained.


## 4. Cramer–Rao Bound

The CRB determines the lower bound on the variances of unbiased parameters estimation. In order to measure the performance of the DP-MUSIC algorithm, the estimation CRB for the dual-polarized conformal array is derived here.The signal model expressed in formula (22) should be converted into a discrete time digital domain, and the probability distribution function (PDF) of L samples is [19](40)pxθ,ϕ,γ,η=12πσn2L/2⋅exp−1σn2⋅∑n=0L−1xn−Aθ,ϕ,γ,ηsnH⋅xn−Aθ,ϕ,γ,ηsn.The array covariance matrixRx contains 4K unknown parameters, they are K azimuth angles, K elevation angles, and 2K polarization parameters. Define the unknown parameter vector embedded in Rx as ξ=θ,ϕ,γ,ηT, where θ=θ1,⋯,θK, ϕ=ϕ1,⋯,ϕK, γ=γ1,⋯,γK, and η=η1,⋯,ηK. Each element of the Fisher information matrix entry can be calculated by using the following formula:(41)Fij=−E∂2lnpxθ,ϕ,γ,η∂ξi∂ξj,i,j=1,⋯,4K.Consequently, the4K×4K Fisher information matrix can be written as(42)F=FθθFθϕFθγFθηFϕθFϕϕFϕγFϕηFγθFγϕFγγFγηFηθFηϕFηγFηη,where Fθθ and Fϕϕ refer to the elevation and azimuth estimation block, respectively. Fγγ and Fηη denote the polarization parameters estimation block, the rest of modules are the cross-correlation estimation block of relevant parameters.Combining formulas (40) and (41), the following equation can be further derived:(43)Fij=L·SNR⋅∂AH∂ξi∂A∂ξj+∂AH∂ξi∂A∂ξj,where SNR=σs2/σn2 and Es2n=σs2. The parameter ξ contains angle parameters and polarization parameters, and their partial derivatives can be calculated by the following formulas:(44)∂A∂θi=∂A˜∂θiP,∂A∂ϕi=∂A˜∂ϕiP,∂A∂γi=A˜∂P∂γi,∂A∂ηi=A˜∂P∂ηi,where(45)∂A˜θ,ϕ∂θi=G∂Tθ,ϕ⋅aθ,ϕ⊗I2∂θi,∂Tθ,ϕ⋅aθ,ϕ⊗I2∂θi=∂Tθ,ϕ∂θi·aθ,ϕ⊗I2+Tθ,ϕ·∂aθ,ϕ⊗I2∂θi,∂Tθ,ϕ∂θi=∂Tcsθ′,ϕ′∂θiRglTscθ,ϕ+Tcsθ′,ϕ′Rgl∂Tscθ,ϕ∂θi.The partial derivative of parametersϕ, γ, and η can be obtained by a similar derivation process. The CRB can be obtained from the inverse of the Fisher information matrix. Define G=F−1, the CRB can be calculated by the following formula:(46)CRBa=12K∑i=12KGii,CRBγ=1K∑i=2K+13KGii,CRBη=1K∑i=3K+14KGii,where CRBa is the Cramer–Rao bound for the DOA. CRBγ and CRBη are the Cramer–Rao bound for polarization parameter.


## 5. Simulation Results

Without loss of generality, an arc conformal array withN = 15 elements is considered as shown in Figure 2. The central angle of the arc is 150°. The antenna element adopts patch antenna model of dual-polarized, and its pattern is [20](47)gθθ′,ϕ′=J2πdsinθ′/λ−J0πdsinθ′/λ·cosϕ′−jsinϕ′,0≤θ′≤π/2,gϕθ′,ϕ′=J2πdsinθ′/λ+J0πdsinθ′/λ·cosθ′sinϕ′−jcosϕ′,0≤θ′≤π/2,gθθ′,ϕ′=gϕθ′,ϕ′=0,θ′>π/2,where J0 and J2 are the first kind of zero-order and second-order Bessel functions, respectively. d=λ/2 is the distance between adjacent elements.Figure 2
Arc conformal array model.In the first simulation, all the signals are assumed to come from the XOY plane. There areK = 3 incident signals with the same power, and the angles of signals are θ1,ϕ1=90°,−40°, θ2,ϕ2=90°,15°, and θ3,ϕ3=90°,40°, respectively. The azimuth scans range from −70° to 70° with the step of 0.1°, the signal-to-noise radio (SNR) is 10 dB, and the number of snapshots are L = 200. The polarization state angles are γ1,η1=20°,60°, γ2,η2=30°,45°, and γ3,η3=60°,30°, respectively.The pseudospectrum is shown in Figure3. Compared with polarization smoothing and initial estimation, the DOA refined estimation has sharper peaks, and it has higher accuracy. It can be seen that the PSA has failed and is not applicable to the dual-polarized conformal array. The estimation values of polarization parameters are obtained by formula (37), and the corresponding spectral peak diagrams are shown in Figures 4, 5, and 6, respectively.Figure 3
The DOA estimation.Figure 4
Polarization estimation result withθ,ϕ=90°,−40°.Figure 5
Polarization estimation result withθ,ϕ=90°,15°.Figure 6
Polarization estimation result withθ,ϕ=90°,40°.The Monte Carlo experiments are used to verify the estimated performance of the proposed method. The root mean square error (RMSE) of the DOA and polarization parameters are defined as(48)RMSEa=1MK∑n=1M​∑i=1K​θi−θ^i,n+ϕi−ϕ^i,n1/2,RMSEγ=1MK∑n=1M∑i=1Kγi−γ^i,n1/2,RMSEη=1MK∑n=1M∑i=1Kηi−η^i,n1/2,where θ^i,n, ϕ^i,n and γ^i,n, η^i,n refer to the DOA estimated value and polarization parameters estimated value of the ith signal in the nth Monte Carlo experiment, respectively. M = 100 is the number of Monte Carlo experiment. The RMSE is compared with CRB to evaluate the performance of parameters estimation in the following simulations.In the second simulation, the SNR changes from −5 dB to 15 dB with the step of 2 dB. The other conditions are the same as the first simulation. Figure7 shows that the RMSE performance of azimuth refined estimation is close to the CRB. Figure 8 shows that corresponding RMSE to the polarization parameters for SNR from −5 dB to 15 dB with the step 2 dB.Figure 7
Angle estimation performances with different SNR.Figure 8
Polarization parameters estimation performances with different SNR.In the third simulation, the number of snapshots change from 100 to 1000 with the step of 100. The SNR is fixed at 0 dB and the other conditions are the same as the first simulation. With the increases of snapshots, Figure9 illustrates the RMSE performance versus the number of snapshots. The RMSE performance of refined estimation is significantly better than the initial estimation. It can be seen from Figure 10 that as the number of snapshots increases, the RMSE of each curve shows a downward trend.Figure 9
Angle estimation performances with different snapshots.Figure 10
Polarization parameters estimation performances with different snapshots.According to Figures7 and 9, the RMSE of DOA initial estimation value and refined estimation value decreases with the increase of the SNR and snapshots, and the error curve of refined estimation approaches the lower bound. Figures 8 and 10 show that the comparison of RMSE performance and CRB for polarization parameters. Through the comparison of above simulation results, it can be seen that the error of angle estimation is smaller than that of polarization parameter estimation. Since there are only two receiving components in the polarization domain while there are N receivers in the space domain, it is reasonable that the estimation performance in the spatial domain is better than the polarization domain. However, the RMSE of the polarization parameters still have a good performance when the SNR and the number of snapshots are large.


## 6. Conclusion

This paper presents the DP-MUSIC algorithm to estimate the polarization and DOA based on the dual-polarized conformal array. Each polarization signal is decomposed into two orthogonal polarization components, which are considered to be a pair of coherent signals. The polarization parameters are modeled as the equivalent coherence coefficients of the orthogonal polarization components. Then, the decoherence method can be used to separate the DOA information coupled with the polarization information. Consequently, the polarization parameters and DOA can be estimated separately by the proposed algorithm. Moreover, the DOA is re-estimated to further improve the DOA estimation accuracy. The DP-MUSIC algorithm can achieve the DOA and polarization estimation for arbitrary polarization signals of the dual-polarized conformal array. Finally, the CRB is derived and simulation results demonstrate the effectiveness of the proposed algorithm.



---

*Source: 8907685-2019-09-18.xml*