# Design of a Broadband Radome-Enclosed Dual-Polarization Antenna Array Covering Sub-6 GHz Band with Differential Feeding

Authors: Zhirong An; Mang He
Journal: International Journal of Antennas and Propagation
 (2020)

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## Abstract

A differentially fed dual-polarized antenna with low cross-polarization is proposed for sub-6 GHz applications. The main patch is fed through two pairs of symmetrical ports, and annular-ring slits are etched around the feedings. The broadband 180° phase shifter provides a stable differential feeding structure, and a 1 mm thick radome with a parasitic patch printed on its inner surface is utilized to expand the impedance bandwidth. The impedance bandwidth of the proposed antenna ranges from 3.3 to 6.0 GHz, covering the entire sub-6 GHz band. The 4-element antenna array features low profile, wide bandwidth, low cross-polarization level, and stable gain over the entire operating band. The prototype of the antenna array is fabricated and measured, and the design is well validated by experimental results.


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## Body

## 1. Introduction

The 3rd Generation Partnership Project (3GPP) has recommended the sub-6 GHz bands (3.3–4.2 GHz and 4.4–5 GHz) [1, 2] and mm-wave frequency bands (24.25–29.5 GHz) [3] as the 5G New Radio (NR) bands. Compared with mm-wave band, sub-6 GHz band has the advantages of less signal attenuation, long transmission distance, and being not easy to be blocked. Therefore, the sub-6 GHz band is more suitable to ensure outdoor signal coverage. On this basis, in order to make full use of spectrum resource, polarization diversity technology has been widely used. As a transmitting or receiving antenna in these communication systems, dual-polarized antenna design is preferred, since it can increase the channel capacity and reduce the multipath fading effect. Meanwhile, low cross-polarization level and high isolation between feeding ports are required, because multiple-input ports are necessary to achieve the dual polarization. Thus, a dual-polarized antenna/array working at sub-6 GHz band with low cross-polarization and high isolation is worth studying.There have been many antenna designs reported for sub-6 GHz applications in recent years [4–21], which can be divided into two types approximately: crossed-dipole antennas and patch antennas. The crossed-dipole antennas usually have the advantage of wide bandwidth; however, due to the limit of the perfect electric conductor (PEC) reflector, these antennas usually have a relatively high profile around 0.25λ0 (λ0 is the free-space wavelength at the center frequency). In [5], a low profile differentially fed dual-polarization antenna is proposed for 5G microcell communications. By introducing an artificial magnetic conductor (AMC) reflector that is composed of annular patches, the profile can be reduced to 0.13λ0. However, the AMC structure increases the cost of fabrication, which limits mass production. Meanwhile, patch antennas have also received extensive attention due to its advantages of low profile and low cost. In [17], a differentially driven dual-polarized patch antenna that utilizes the intersected open-loop resonators is proposed for wireless communication systems. In [19], a dual-band dual-polarization filtering antenna is achieved by employing the coupled resonator technique. However, due to the low profile and planar configuration, patch antennas normally face the problem of limited bandwidth, which makes it difficult to meet the bandwidth requirement for sub-6 GHz applications. In [20], combined with differential feeding scheme, a dual-polarized antenna achieves a wider bandwidth of 26% (3–3.9 GHz) with low profile of 0.13λ0; however, this bandwidth is still not adequate to cover the entire sub-6 GHz band.In this paper, the design of a broadband dual-polarized antenna that works stably throughout the entire sub-6 GHz band is proposed. Not only has the effect of the radome been taken into consideration in the design, but also the radome structure is utilized to expand the impedance bandwidth of the antenna. This integrated design results in a very wide bandwidth ranging from 3.3 to 6 GHz. Owing to the differential feeding technique, the 1 × 4 antenna array possesses low cross-polarization, high isolation, stable gain, and radiation pattern within the entire frequency band.


## 2. Antenna Design

### 2.1. Antenna Element

Figure1 shows the geometry of the antenna element. The main radiator is a square patch that is printed on an FR4 substrate (εr = 4.4, tanδ = 0.02) with the thickness H1. The patch has the side length of W1 and is differentially fed through four ports (named ports 1 to 4). Each port is P1 distant from the patch’s center and is connected to the ground via a metallized via hole. In addition, an annular-ring slit with the inner diameter D1 is etched from the patch around each via hole for convenient tuning of the antenna’s input impedance. Above the main patch, an FR4 slab with the thickness H3 is used as the radome to protect the antenna from outside environments. To maintain a low profile of the entire antenna structure, the space H2 between the radome and the main radiator should not be large. Therefore, due to the close proximity between them, the radome has significant effects on the radiation performance of the main patch. However, in this design, we utilize the positive role of the radome and print a parasitic square patch with the side length W2 on the inner surface of it to build a stacked patch structure for bandwidth expansion. Through exhaustive parametric study, the optimum dimensions of the antenna element are obtained and listed in Table 1 for reference.Figure 1
Configuration of the antenna element.Table 1
Optimum dimensions of the antenna element (unit: mm).
ParameterW1W2D1P1H1H2H3Values12.513.215.231.51


### 2.2. Working Principle

Since the antenna is fed differentially through two pairs of symmetrical ports, the proposed antenna is a single-ended four-port network, as shown in Figure2(a). According to the definition of S-parameters, we have(1)b=Sa.Figure 2
Four-port network and differential two-port network model of the antenna element.
(a)(b)At the same time, when ports 1 and 2 are excited with equal magnitude and 180° phase difference, they can be considered as a pair of differential port (named port A) [22]. Similarly, ports 3 and 4 can also be regarded as the differential port B. As defined in [22], the antenna is actually a two-port differential network, as shown in Figure 2(b). At this time, we have(2)bdAbdB=SddAASddABSddBASddBB⋅adAadB,where(3)bdA=b1−b2,bdB=b3−b4,adA=a1−a2,adB=a3−a4.Considering the differential portA, when ports 1 and 2 are differentially excited while port 3 and 4 are connected to 50 Ω loadings, the differential S-parameters can be defined:(4)SddAA=bdAadA|adB=0=12S11−S12−S21+S22,SddBA=bdBadA|adB=0=12S31−S32−S41+S42.Similarly, we get(5)SddAB=bdAadB|adA=0=12S13−S14−S23+S24,SddBA=bdBadB|adA=0=12S33−S34−S43+S44.On the basis of the above discussion, the antenna design can be carried out as follows: First, only single-layer patch antenna is considered, as shown in Figure3, Ref1. The length of the main patch is W1 = 12.5 mm, which is about 1/2 λg at 5.3 GHz (λg is the guided wavelength). On this basis, annular-ring slits are etched around the feedings [23], as shown in Figure 4, Ref2. The annular-ring slits change the impedance characteristics of the feeding point, causing the input impedance curve of the antenna surrounding the origin on the Smith chart. Next, a radome is added above the main patch, as shown in Figure 4, Ref3. As shown in Figures 4(b) and 4(c), the radome has the effect of impedance matching, thereby improving the impedance bandwidth of the antenna. As shown in Figure 4(a), the antenna shown in Ref3 is still poorly matched at low frequencies (3.3–3.5 GHz). For this reason, a large-sized parasitic patch is printed on the lower surface of the radome, thereby improving the impedance matching at low frequencies, which makes the antenna cover the entire sub-6 GHz band. The parametric studies of the antenna parameters are shown in Figure 5.Figure 3
Simulated (S)ddAA, Zin, and Smith chart of the single-layer patch antenna.
(a)(b)(c)Figure 4
Simulated (S)ddAA, Zin, and Smith chart of different antennas.
(a)(b)(c)(d)Figure 5
Parametric studies of the proposed antenna by changing the values of (a)W2, (b) H2, and (c) H3.
(a)(b)(c)The current distribution on the patch is relatively consistent throughout the entire frequency band, and no high-order modes were generated. Taking 5 GHz as an example, the current distribution is shown in Figure6. When port A is differentially fed, the current direction is along the x-direction; and, symmetrically, when port B is differentially fed, the current direction is along the y-direction. Thereby, two orthogonally polarized waves are generated. Meanwhile, the proposed antenna has a high port isolation, as shown in Figure 7. Because the antenna structure is symmetrical, S31 equals S41 and S32 is equal to S42 according to the network theory. Thus, SddBA should be zero from equation (4), which means that high isolation is a natural result of the differential feeding scheme. Figure 6 can also be used to illustrate this point, in which when the differential port A is fed, the current near ports 3 and 4 is completely symmetrical. This indicates that the potential difference between the two ports is zero, and no current will flow into ports 3 and 4, which leads to a high isolation between two differential ports.Figure 6
Current distributions on the main patch and the parasitic patch when portA is fed differentially: (a) main patch and (b) parasitic patch.
(a)(b)Figure 7
Simulated differential (S)-parameters of proposed antenna.Figure8 shows the simulated gain and cross-polarization level of the antenna at the broadside direction. Due to the differential feeding, on the two half patches, the direction of the currents that are orthogonal to the main currents is opposite, so the cross-polarization radiation can be very low. Within the entire sub-6 GHz band, the cross-polarization level is less than −45 dB. The simulated radiation pattern of the antenna at two typical frequencies in the 5G NR band is shown in Figure 9, and the maximum cross-polarization is observed to be less than −36 dB within the space of solid angle θ ≤ 60°.Figure 8
Simulated gain and cross-polarization of the antenna at the broadside direction.Figure 9
Simulated radiation patterns of the antenna at two different frequencies. (a) 3.5 GHz; (b) 5 GHz.
(a)(b)


### 2.3. Feeding Network

As seen in the last subsection, the antenna will maintain very stable performance if the feeding provides ideal differential signal. Therefore, it is extremely important for the feeding network to output two stable signals with equal magnitude and reverse phase within a very wide band that can cover the entire sub-6 GHz frequencies. In this design, we use the feeding network that is shown in Figure10. The network consists of a simple T-type power divider with one phase shifter cascading on each of the two output branches. The phase shifter adopts a transition structure from microstrip line to ground slot [24]. As shown in Figure 11, the current transmits along the microstrip line (A1–B1 or A2–B2) and then couples to the slot through a microstrip-slot transition structure at point B1 or B2 and then transmits along the slot (B1–C1 or B2–C2) until it is coupled to the microstrip line at point C1 or C2. Since the coupling direction is opposite at C1 and C2 with reference to the direction of electric field (marked as + and – in Figure 11), 180° phase difference is introduced between the two branches. Moreover, the total length of the two branches is approximately identical (A1–D1 and A2–D2), so, compared with traditional phase shifters, the output signals at the end of two branches (i.e., at the points D1 and D2) have the same magnitude and 180° phase difference almost independent of frequency. In addition, the impedance matching of the structure can be finely tuned by changing the radius of the circular stub (R1 and R2), as shown in Figure 12. The simulated S-parameters of the feeding network are shown in Figure 13. It is seen that the transmission loss ranges from −3.60 to −3.13 dB, which is mainly due to the relatively large dielectric loss of the low-cost FR4 substrate (tanδ = 0.02). Within the entire frequency band, the return loss is better than 12 dB and the phase difference of the two output ports is 180° ± 0.8°, which shows very stable broadband phase shift performance.Figure 10
Configuration of the feeding network.Figure 11
Distribution of current and electric field of the feeding network.Figure 12
Parametric studies of the feeding network by changing the values of (a)R1 and (b) R2.
(a)(b)Figure 13
Simulated (S)-parameters and phase difference of the feeding network.


## 2.1. Antenna Element

Figure1 shows the geometry of the antenna element. The main radiator is a square patch that is printed on an FR4 substrate (εr = 4.4, tanδ = 0.02) with the thickness H1. The patch has the side length of W1 and is differentially fed through four ports (named ports 1 to 4). Each port is P1 distant from the patch’s center and is connected to the ground via a metallized via hole. In addition, an annular-ring slit with the inner diameter D1 is etched from the patch around each via hole for convenient tuning of the antenna’s input impedance. Above the main patch, an FR4 slab with the thickness H3 is used as the radome to protect the antenna from outside environments. To maintain a low profile of the entire antenna structure, the space H2 between the radome and the main radiator should not be large. Therefore, due to the close proximity between them, the radome has significant effects on the radiation performance of the main patch. However, in this design, we utilize the positive role of the radome and print a parasitic square patch with the side length W2 on the inner surface of it to build a stacked patch structure for bandwidth expansion. Through exhaustive parametric study, the optimum dimensions of the antenna element are obtained and listed in Table 1 for reference.Figure 1
Configuration of the antenna element.Table 1
Optimum dimensions of the antenna element (unit: mm).
ParameterW1W2D1P1H1H2H3Values12.513.215.231.51


## 2.2. Working Principle

Since the antenna is fed differentially through two pairs of symmetrical ports, the proposed antenna is a single-ended four-port network, as shown in Figure2(a). According to the definition of S-parameters, we have(1)b=Sa.Figure 2
Four-port network and differential two-port network model of the antenna element.
(a)(b)At the same time, when ports 1 and 2 are excited with equal magnitude and 180° phase difference, they can be considered as a pair of differential port (named port A) [22]. Similarly, ports 3 and 4 can also be regarded as the differential port B. As defined in [22], the antenna is actually a two-port differential network, as shown in Figure 2(b). At this time, we have(2)bdAbdB=SddAASddABSddBASddBB⋅adAadB,where(3)bdA=b1−b2,bdB=b3−b4,adA=a1−a2,adB=a3−a4.Considering the differential portA, when ports 1 and 2 are differentially excited while port 3 and 4 are connected to 50 Ω loadings, the differential S-parameters can be defined:(4)SddAA=bdAadA|adB=0=12S11−S12−S21+S22,SddBA=bdBadA|adB=0=12S31−S32−S41+S42.Similarly, we get(5)SddAB=bdAadB|adA=0=12S13−S14−S23+S24,SddBA=bdBadB|adA=0=12S33−S34−S43+S44.On the basis of the above discussion, the antenna design can be carried out as follows: First, only single-layer patch antenna is considered, as shown in Figure3, Ref1. The length of the main patch is W1 = 12.5 mm, which is about 1/2 λg at 5.3 GHz (λg is the guided wavelength). On this basis, annular-ring slits are etched around the feedings [23], as shown in Figure 4, Ref2. The annular-ring slits change the impedance characteristics of the feeding point, causing the input impedance curve of the antenna surrounding the origin on the Smith chart. Next, a radome is added above the main patch, as shown in Figure 4, Ref3. As shown in Figures 4(b) and 4(c), the radome has the effect of impedance matching, thereby improving the impedance bandwidth of the antenna. As shown in Figure 4(a), the antenna shown in Ref3 is still poorly matched at low frequencies (3.3–3.5 GHz). For this reason, a large-sized parasitic patch is printed on the lower surface of the radome, thereby improving the impedance matching at low frequencies, which makes the antenna cover the entire sub-6 GHz band. The parametric studies of the antenna parameters are shown in Figure 5.Figure 3
Simulated (S)ddAA, Zin, and Smith chart of the single-layer patch antenna.
(a)(b)(c)Figure 4
Simulated (S)ddAA, Zin, and Smith chart of different antennas.
(a)(b)(c)(d)Figure 5
Parametric studies of the proposed antenna by changing the values of (a)W2, (b) H2, and (c) H3.
(a)(b)(c)The current distribution on the patch is relatively consistent throughout the entire frequency band, and no high-order modes were generated. Taking 5 GHz as an example, the current distribution is shown in Figure6. When port A is differentially fed, the current direction is along the x-direction; and, symmetrically, when port B is differentially fed, the current direction is along the y-direction. Thereby, two orthogonally polarized waves are generated. Meanwhile, the proposed antenna has a high port isolation, as shown in Figure 7. Because the antenna structure is symmetrical, S31 equals S41 and S32 is equal to S42 according to the network theory. Thus, SddBA should be zero from equation (4), which means that high isolation is a natural result of the differential feeding scheme. Figure 6 can also be used to illustrate this point, in which when the differential port A is fed, the current near ports 3 and 4 is completely symmetrical. This indicates that the potential difference between the two ports is zero, and no current will flow into ports 3 and 4, which leads to a high isolation between two differential ports.Figure 6
Current distributions on the main patch and the parasitic patch when portA is fed differentially: (a) main patch and (b) parasitic patch.
(a)(b)Figure 7
Simulated differential (S)-parameters of proposed antenna.Figure8 shows the simulated gain and cross-polarization level of the antenna at the broadside direction. Due to the differential feeding, on the two half patches, the direction of the currents that are orthogonal to the main currents is opposite, so the cross-polarization radiation can be very low. Within the entire sub-6 GHz band, the cross-polarization level is less than −45 dB. The simulated radiation pattern of the antenna at two typical frequencies in the 5G NR band is shown in Figure 9, and the maximum cross-polarization is observed to be less than −36 dB within the space of solid angle θ ≤ 60°.Figure 8
Simulated gain and cross-polarization of the antenna at the broadside direction.Figure 9
Simulated radiation patterns of the antenna at two different frequencies. (a) 3.5 GHz; (b) 5 GHz.
(a)(b)


## 2.3. Feeding Network

As seen in the last subsection, the antenna will maintain very stable performance if the feeding provides ideal differential signal. Therefore, it is extremely important for the feeding network to output two stable signals with equal magnitude and reverse phase within a very wide band that can cover the entire sub-6 GHz frequencies. In this design, we use the feeding network that is shown in Figure10. The network consists of a simple T-type power divider with one phase shifter cascading on each of the two output branches. The phase shifter adopts a transition structure from microstrip line to ground slot [24]. As shown in Figure 11, the current transmits along the microstrip line (A1–B1 or A2–B2) and then couples to the slot through a microstrip-slot transition structure at point B1 or B2 and then transmits along the slot (B1–C1 or B2–C2) until it is coupled to the microstrip line at point C1 or C2. Since the coupling direction is opposite at C1 and C2 with reference to the direction of electric field (marked as + and – in Figure 11), 180° phase difference is introduced between the two branches. Moreover, the total length of the two branches is approximately identical (A1–D1 and A2–D2), so, compared with traditional phase shifters, the output signals at the end of two branches (i.e., at the points D1 and D2) have the same magnitude and 180° phase difference almost independent of frequency. In addition, the impedance matching of the structure can be finely tuned by changing the radius of the circular stub (R1 and R2), as shown in Figure 12. The simulated S-parameters of the feeding network are shown in Figure 13. It is seen that the transmission loss ranges from −3.60 to −3.13 dB, which is mainly due to the relatively large dielectric loss of the low-cost FR4 substrate (tanδ = 0.02). Within the entire frequency band, the return loss is better than 12 dB and the phase difference of the two output ports is 180° ± 0.8°, which shows very stable broadband phase shift performance.Figure 10
Configuration of the feeding network.Figure 11
Distribution of current and electric field of the feeding network.Figure 12
Parametric studies of the feeding network by changing the values of (a)R1 and (b) R2.
(a)(b)Figure 13
Simulated (S)-parameters and phase difference of the feeding network.


## 3. Antenna Array and Results

As shown in Figure14, a 4-element linear array is designed, and the prototype is fabricated and measured for possible use in sub-6 GHz applications. The interelement spacing is 40 mm, corresponding to 0.62λ0 (λ0 is the free-space wavelength at the center frequency 4.65 GHz of the sub-6 GHz band). All the measurements are carried out using the multiprobe wireless communication test system RayZone 1800. Figure 15 shows the simulated and measured S-parameters of the antenna array. It is seen that the measured results agree well with the simulated ones, and throughout the 3.3–6.0 GHz frequency range the measured reflection coefficients at the two feeding ports are less than −10 dB and the port isolation is greater than 33 dB. The simulated and measured peak gain and total efficiency of the array, when only the differential port A is fed and the other port is connected to a matched load, are shown in Figure 16. The measured cross-polarization is lower than −30 dB within the entire frequency band. Compared to the simulation results of the antenna element, both the cross-polarization level and the port isolation are slightly deteriorated due to the feeding network because it introduces asymmetry between two ports in some extent, which may raise the cross-polarization radiation and reduce the port isolation. It is also found in Figure 16 that the total efficiency of the antenna maintains above 65% within the entire operating frequency band despite the use of low-cost FR4 substrate with large dielectric loss. Figure 17 shows the radiation patterns of the proposed array at two different frequencies 3.5 and 5.0 GHz when only the differential port A is fed, in which the xoz-plane is defined as the V-plane (vertical plane) and the yoz-plane is defined as the H-plane (horizontal plane). It is clear that the radiation pattern is stable and the cross-polarization level is lower than −35 dB at the two frequencies.Figure 14
Simulation model and fabricated prototype of the 1 × 4 antenna array. (a) Simulation model, (b) top view, (c) back view, and (d) side view of the fabricated prototype.
(a)(b)(c)(d)Figure 15
Simulated and measured (S)-parameters of the antenna array.Figure 16
Simulated and measured gain and efficiency of the antenna array.Figure 17
Simulated and measured radiation patterns of the antenna array at (a) 3.5 GHz and (b) 5.0 GHz.
(a)(b)Table2 shows comparison of the measured performance of the proposed antenna array with the existing works. Compared with the previous designs, the proposed antenna has the widest bandwidth from 3.3 to 6.0 GHz, which can cover the entire sub-6 GHz band. It also has the lowest cross-polarization level, which is −30 dB. At the same time, it has acceptable gain and efficiency compared with [5, 19]. The proposed antenna retains low profile even with the radome being considered, which makes the present design a potential base-station antenna.Table 2
Comparison of the proposed antenna array with previous works.
RefsOperating bands (GHz)Height (mm)Size (mm2/λ02)Isolation (dB)Element gain (dB)EfficiencyCross-polarization (dB)Radome integrated[4]3.3–3.618.826 × 26257.3>89.3%−17/−24.5No8.7%0.216λ00.3 × 0.3[5]3.28–5.3110.596 × 96376.3>65.0%−20No47.3%0.15λ01.37 × 1.37[16]5.4–5.65.319.5 × 16.8259.5—−19.5Yes3.6%0.097λ00.36 × 0.31[17]3.3–3.665.81380 × 80358.2—−20.8No10.3%0.067λ00.93 × 0.93[18]3.3–3.66.825.2 × 25.2268.5—−22Yes8.7%0.078λ00.29 × 0.29[19]4.1–4.35—50 × 50286.5—−25No5.8–6.15—1 × 130−155.9%/5.9%—[20]3.14–3.811.882 × 82438.1>78%−30No16.6%0.136λ00.95 × 0.95[25]3.28–3.7111.365 × 65378.34—−18.2No4.8–5.180.13λ00.75 × 0.7512.3%/7.6%[26]3.12–3.911.365 × 6535.28.1—−21No22.2%0.15λ00.7 × 0.7[5]3.26–3.739.596 × 96259.1>65%−20No4.68–5.050.13λ01.34 × 1.3413.5%/7.6%This work3.3–6.06.345 × 80336.4>65%−30Yes58.1%0.097λ00.7 × 1.2


## 4. Conclusion

A broadband dual-polarized antenna array covering the entire sub-6 GHz band is proposed. In the design of antenna element and array, the advantageous side of the dielectric radome is utilized, and a parasitic patch is etched on its inner surface, which greatly expands the bandwidth of the antenna. The use of differential feeding technique, square-shaped main and parasitic patches, and broadband feeding network maintains good symmetry of the antenna structure, resulting in very low cross-polarization level and high isolation between feeding ports within the entire frequency band. Experimental results verify the proposed design, and the antenna array may be a good candidate for base-station applications.



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*Source: 8881317-2020-12-01.xml*