# Underground Communications Using Capacitive Data Transfer Devices

Authors: Shaoge Zang; Keran Hou; Sing Kiong Nguang
Journal: Journal of Sensors
 (2020)

---

## Abstract

This paper explores the feasibility of applying the capacitive power transfer (CPT) technology in underground data transmission applications. Based on the electrical properties of soils, the paper extends the existing CPT air coupler model into a more generalized model. The autonomous push-pull inverter is selected to power the CPT system and modified to further the data transmission range. With a designed load shift keying (LSK) circuitry, this self-oscillating inverter regards the data as a sequence of impedance changes, resulting in operation frequency drifts. A Frequency Shift Keying (FSK) demodulator is applied to capture the frequency variations and recover back to data. The proposed design has been simulated, verified, and implemented on a complete prototype. Various testings have been carried out, and the results are satisfactory.


---

## Body

## 1. Introduction

Smart farming and precision agriculture are drawing increasing popularity over the last several years. This new farming concept integrates the Internet of Things (IoT) to improve harvest productivity with a more sustainable farming practice [1, 2]. Underground sensors then have been widely used and developed to accommodate the needs. The sensors play an essential role in monitoring soil nutrition levels, water concentrations, environmental hazards, etc.With a massive sensor deployment scale, data collection can be challenging. Rather than using physical wire to connect between sensors for retrieving data, wireless communication is a sensible option in favour of its flexibility and convenience. It allows users to do real-time monitoring on the plants and the sensors. Nevertheless, data transfer through soils could be a difficult task. Conventional Radio Frequency (RF) modules are not suitable for underground communications as the signal can be highly attenuated due to the electrical properties of soils (e.g., electrical conductivity and electrical permittivity) [3]. Moreover, the texture of soils can be primarily affected by weather, geographical locations, insects, etc., leading to a worse performance [4].Currently, two technologies are mostly applied in the underground communications: electromagnetic wave (EM) and Magnetic Induction (MI) [5–7]. The working principle of EM technology is the same as RF modules. It uses a much lower frequency to minimize the path loss due to the soil electrical properties. The performance and flexibility of the EM technology are limited to its relatively high-power consumption and antenna sizes [8, 9]. In another study, MI uses a pair of inductively coupled coils to transmit the data. The magnetic fields generated by the transmitting coil will induce a voltage on the receiving end [10]. The performance of MI is heavily dependent on the alignment of the coils. The coils need to be aligned face to face perfectly to get maximum transmission range [5].CPT is an alternative method to achieve wireless power transfer (WPT) and data transfer [11]. A standard CPT system has four metal plates to form a capacitive coupling. The power is transferred between the plates via electric fields. Compared to the MI technology, CPT systems have advantages in terms of lightweight and low cost [12, 13]. They barely suffer from eddy current losses in high-frequency magnetic fields when there is metallic material nearby [14]. Besides, the CPT systems are found to have a better misalignment performance [15, 16]. Several research groups have already attempted to use CPT to achieve data transmission in some industrial applications [17, 18]. Compared to the EM technology, the CPT system can be more energy-efficient and easier to design. With proper designs, it can achieve both wireless data and power delivery [19], which can significantly extend the battery life.Motivated by merits of the CPT technology, this paper explores the feasibility to apply the CPT in underground data transmission. This paper modifies the current air capacitor coupler model in studies [17–19] into a more generalized underground impedance coupler model to describe the electrical characteristics of soils. Based on the modified model, we introduced load shift keying (LSK) circuitry on the sensor side. The data then can be modulated by switching a load on the sensor side, causing an impedance change to the system. Due to the unique working principle of the push-pull inverter, the impedance change will result in an inverter operation frequency drift. These frequency variations are captured by Frequency Shift Keying (FSK) circuitry on the receiving end and recovered into data. In such way, the battery life of sensors can be extensively increased as they only consume a small amount of current to drive the load switch. An additional transformer is used in the push-pull inverter to boost up the output voltage, which further improves the data transmission range. Besides, the transformer replaces the resonant component in the inverter topology and makes it more compact. A comprehensive system circuit model is built and simulated. The performance of the proposed CPT data transfer system has been tested under various conditions. The experimental results indicate a promising sign.The main contribution of this paper can be summarized as follows:(i)
Analyze the soil electrical properties and extend the standard CPT model to a more generalized model(ii)
Build a comprehensive circuit simulation model of the push-pull inverter that incorporates the soil electrical properties(iii)
Achieve underground data transfer via FSK modulation with the push-pull inverterThe paper is structured as follows: In Section1, the difference between the air coupler model and the underground coupler model is presented in the simulation. A more generalized circuit model is derived based on existing studies. Section 2 elaborates the proposed CPT data transfer system based on the push-pull inverter. In Section 3, multiple testings have been carried out, and the experiment results are presented. The conclusion is drawn in Section 4.


## 2. Underground Impedance Coupler Model

In this section, the underground coupler setup is presented. With the same coupler setup, the authors firstly compare the electrical property difference of using air and soils as the mediums. The results are simulated and visualized in the electromagnetic software CST. Based on the simulation results, the paper modifies the current air coupler model to a more generalized model to suit the proposed application.


### 2.1. Underground Plate Configuration

The underground impedance coupler configuration is illustrated in Figure1. A standard four-plate CPT system is used in this paper. The radius of each plate is labelled as ri, where i=1,2,3,4. Two round plates P1 and P2 are placed on the primary side, and the distance between two primary plates is marked as lpp. Similarly, lss is the distance between P3 and P4 on the secondary side. The lateral distance between the two sides is tagged as lps. The misalignment lmis is the difference between two midpoints of lpp and lss.Figure 1
Demonstration of the plate arrangements.Soil is commonly known to be conductive and can be modelled as an infinite amount of capacitive and conductive lumped elementsRlumped and Clumped connected in parallel. Ignoring the fringing effect, the impedance of every “lump” of a cross-sectional area of δA and a length of δd can be approximated as
(1)Zlump=δdδAσεrε0s1/σ+1/εrε0s,where s=2πfj, ε0=8.854×10−12F/m, εr is the relative permittivity, and σ is the conductivity of the dielectric medium.Simulation has been conducted in the CST software. CST is a high-performance 3D electromagnetic analysis software package for designing, analyzing, and optimizing electromagnetic components and systems [20]. The soil property was set from the source [21], where silty soil with 30% water content was chosen. Two identical round metal plates with diameters of 7cm are placed 7cm away from each other. A sinusoidal excitation voltage of 1MHz is applied to one of the plates.Figure2 shows the electric field distributions of couplers with air and soils as the medium and their equivalent circuit models. Simulation results are summarized in Table 1.Figure 2
CST simulation results.
(a)
E-field distributions(b)
Equivalent circuit modelsTable 1
CST simulation results.
MediumFrequencyCapacitanceResistanceReactanceImpedancePhaseAir1 MHz2.156 pF0Ω73.8 kΩ73.8 kΩ-1.57 radSoil1 MHz34.85 pF6.82 kΩ4.57 kΩ3.795 kΩ-0.981 radFrom Table1, it can be seen that the air coupler is purely capacitive with an impedance of 73.8 kΩ. On the contrary, with soil as the medium, the resulting impedance is of 3.795 kΩ at −0.981 radians. It is equivalent to a resistor of 6.82 kΩ and a capacitor of 34.85 pF connected in parallel.The soil behaves as a lossy dielectric. The real part of dielectric constant contributes to the capacitive reactance of soil while the imaginary dielectric constant is the loss. The standard air coupler model in current CPT studies cannot be applied and needs modifications.


### 2.2. Improved Underground Coupler Model for Soil Condition

In current CPT studies, the air couplers are modelled by introducing the capacitors between any two plates. With four plates, it forms a network with six capacitors. We improved the original model by replacing capacitors with corresponding impedances, as depicted in Figure3. The impedance has both the resistive part and the capacitive part to describe the electrical characteristics of the soils.Figure 3
Coupler model.
(a)
Original coupler model(b)
Improved coupler model for soilsTo analyze the circuits in Figure3, we define Vp1,Vp2,Vp3, and Vp4 as the voltages on each plate, respectively. Set Vp2=0 as the electrical reference and apply Kirchhoff’s current law (KCL), the following equations could be obtained:
(2)I1=Vp1−Vp2Z12+Vp1−Vp3Z13+Vp1−Vp4Z14,I2=Vp3−Vp4Z34+Vp3−Vp2Z23−Vp1−Vp3Z13.SinceV1=Vp1−Vp2 and V2=Vp3−Vp4, the transfer function of V2/V1 can be derived:
(3)H1,2=Z12Z23Z14−Z13Z24ZD1,where
(4)ZD1=Z13Z23Z14+Z13Z23Z24+Z13Z14Z24+Z13Z23Z12+Z23Z14Z24+Z13Z24Z12+Z23Z14Z12+Z14Z24Z12.The input impedanceZin,pri=V1/I1 can be expressed as
(5)Zin,pri=Z12Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z13Z14Z34+Z14Z23Z24+Z13Z24Z34+Z14Z23Z34+Z23Z24Z34Z12Z13Z23+Z12Z13Z24+Z12Z14Z23+Z12Z14Z24+Z13Z14Z23+Z13Z14Z24+Z12Z13Z34+Z12Z14Z34+Z13Z23Z24+Z13Z14Z34+Z14Z23Z24+Z12Z23Z34+Z12Z24Z34+Z13Z24Z34+Z14Z23Z34+Z23Z24Z34.It should be noticed that the impedance network is no longer linear. Therefore, the reciprocal principle for a two-port system cannot be applied. In other words,H1,2≠H2,1−1. The transfer function of V1/V2 can be expressed as
(6)H2,1=Z34Z14Z23−Z13Z24ZD2,where
(7)ZD2=Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z13Z14Z34+Z14Z23Z24+Z13Z24Z34+Z14Z23Z34+Z23Z24Z34.The input impedance on the secondary sideZin,sec is described as
(8)Zin,sec=Z34Z13Z23Z14+Z13Z23Z24+Z13Z14Z24+Z13Z23Z12+Z14Z23Z24+Z12Z13Z24+Z12Z14Z23+Z12Z14Z24Z13Z14Z34+Z13Z24Z34+Z14Z23Z34+Z23Z24Z34+Z13Z14Z23+Z13Z23Z24+Z12Z13Z34+Z12Z23Z34+Z13Z14Z24+Z12Z13Z23+Z14Z23Z24+Z12Z14Z34+Z12Z24Z34+Z12Z13Z24+Z12Z14Z23+Z12Z14Z24.Similar to the analysis in study [16], the circuit is simplified into an equivalent π model as shown in Figure 4. As the model is asymmetrical, the components ZM1,ZM2,Zint1, and Zint2 need to be considered separately. The input impedance can be described as
(9)Zin,pri=Zint1ZM1+ZM2+Zint2ZM1+ZM2+Zint1+Zint2,Zin,sec=Zint2ZM1+ZM2+Zint1ZM1+ZM2+Zint1+Zint2.Figure 4
π model for underground couplers.The transfer functions can be expressed as(10)H1,2=Zint2ZM1+ZM2+Zint2,(11)H1,2=Zint2ZM1+ZM2+Zint2.By solving Equations (3)–(11), the component value in the π model can be obtained:
(12)ZM=Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z14Z23Z24Z14Z23−Z13Z24,Zint1=Z12Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z14Z23Z24Z12Z13Z23+2Z12Z13Z24+Z12Z14Z24+Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z14Z23Z24,Zint2=Z34Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z14Z23Z24Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z13Z14Z34+Z14Z23Z24+2Z13Z24Z34+Z23Z24Z34,where ZM=ZM1+ZM2.


## 2.1. Underground Plate Configuration

The underground impedance coupler configuration is illustrated in Figure1. A standard four-plate CPT system is used in this paper. The radius of each plate is labelled as ri, where i=1,2,3,4. Two round plates P1 and P2 are placed on the primary side, and the distance between two primary plates is marked as lpp. Similarly, lss is the distance between P3 and P4 on the secondary side. The lateral distance between the two sides is tagged as lps. The misalignment lmis is the difference between two midpoints of lpp and lss.Figure 1
Demonstration of the plate arrangements.Soil is commonly known to be conductive and can be modelled as an infinite amount of capacitive and conductive lumped elementsRlumped and Clumped connected in parallel. Ignoring the fringing effect, the impedance of every “lump” of a cross-sectional area of δA and a length of δd can be approximated as
(1)Zlump=δdδAσεrε0s1/σ+1/εrε0s,where s=2πfj, ε0=8.854×10−12F/m, εr is the relative permittivity, and σ is the conductivity of the dielectric medium.Simulation has been conducted in the CST software. CST is a high-performance 3D electromagnetic analysis software package for designing, analyzing, and optimizing electromagnetic components and systems [20]. The soil property was set from the source [21], where silty soil with 30% water content was chosen. Two identical round metal plates with diameters of 7cm are placed 7cm away from each other. A sinusoidal excitation voltage of 1MHz is applied to one of the plates.Figure2 shows the electric field distributions of couplers with air and soils as the medium and their equivalent circuit models. Simulation results are summarized in Table 1.Figure 2
CST simulation results.
(a)
E-field distributions(b)
Equivalent circuit modelsTable 1
CST simulation results.
MediumFrequencyCapacitanceResistanceReactanceImpedancePhaseAir1 MHz2.156 pF0Ω73.8 kΩ73.8 kΩ-1.57 radSoil1 MHz34.85 pF6.82 kΩ4.57 kΩ3.795 kΩ-0.981 radFrom Table1, it can be seen that the air coupler is purely capacitive with an impedance of 73.8 kΩ. On the contrary, with soil as the medium, the resulting impedance is of 3.795 kΩ at −0.981 radians. It is equivalent to a resistor of 6.82 kΩ and a capacitor of 34.85 pF connected in parallel.The soil behaves as a lossy dielectric. The real part of dielectric constant contributes to the capacitive reactance of soil while the imaginary dielectric constant is the loss. The standard air coupler model in current CPT studies cannot be applied and needs modifications.


## 2.2. Improved Underground Coupler Model for Soil Condition

In current CPT studies, the air couplers are modelled by introducing the capacitors between any two plates. With four plates, it forms a network with six capacitors. We improved the original model by replacing capacitors with corresponding impedances, as depicted in Figure3. The impedance has both the resistive part and the capacitive part to describe the electrical characteristics of the soils.Figure 3
Coupler model.
(a)
Original coupler model(b)
Improved coupler model for soilsTo analyze the circuits in Figure3, we define Vp1,Vp2,Vp3, and Vp4 as the voltages on each plate, respectively. Set Vp2=0 as the electrical reference and apply Kirchhoff’s current law (KCL), the following equations could be obtained:
(2)I1=Vp1−Vp2Z12+Vp1−Vp3Z13+Vp1−Vp4Z14,I2=Vp3−Vp4Z34+Vp3−Vp2Z23−Vp1−Vp3Z13.SinceV1=Vp1−Vp2 and V2=Vp3−Vp4, the transfer function of V2/V1 can be derived:
(3)H1,2=Z12Z23Z14−Z13Z24ZD1,where
(4)ZD1=Z13Z23Z14+Z13Z23Z24+Z13Z14Z24+Z13Z23Z12+Z23Z14Z24+Z13Z24Z12+Z23Z14Z12+Z14Z24Z12.The input impedanceZin,pri=V1/I1 can be expressed as
(5)Zin,pri=Z12Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z13Z14Z34+Z14Z23Z24+Z13Z24Z34+Z14Z23Z34+Z23Z24Z34Z12Z13Z23+Z12Z13Z24+Z12Z14Z23+Z12Z14Z24+Z13Z14Z23+Z13Z14Z24+Z12Z13Z34+Z12Z14Z34+Z13Z23Z24+Z13Z14Z34+Z14Z23Z24+Z12Z23Z34+Z12Z24Z34+Z13Z24Z34+Z14Z23Z34+Z23Z24Z34.It should be noticed that the impedance network is no longer linear. Therefore, the reciprocal principle for a two-port system cannot be applied. In other words,H1,2≠H2,1−1. The transfer function of V1/V2 can be expressed as
(6)H2,1=Z34Z14Z23−Z13Z24ZD2,where
(7)ZD2=Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z13Z14Z34+Z14Z23Z24+Z13Z24Z34+Z14Z23Z34+Z23Z24Z34.The input impedance on the secondary sideZin,sec is described as
(8)Zin,sec=Z34Z13Z23Z14+Z13Z23Z24+Z13Z14Z24+Z13Z23Z12+Z14Z23Z24+Z12Z13Z24+Z12Z14Z23+Z12Z14Z24Z13Z14Z34+Z13Z24Z34+Z14Z23Z34+Z23Z24Z34+Z13Z14Z23+Z13Z23Z24+Z12Z13Z34+Z12Z23Z34+Z13Z14Z24+Z12Z13Z23+Z14Z23Z24+Z12Z14Z34+Z12Z24Z34+Z12Z13Z24+Z12Z14Z23+Z12Z14Z24.Similar to the analysis in study [16], the circuit is simplified into an equivalent π model as shown in Figure 4. As the model is asymmetrical, the components ZM1,ZM2,Zint1, and Zint2 need to be considered separately. The input impedance can be described as
(9)Zin,pri=Zint1ZM1+ZM2+Zint2ZM1+ZM2+Zint1+Zint2,Zin,sec=Zint2ZM1+ZM2+Zint1ZM1+ZM2+Zint1+Zint2.Figure 4
π model for underground couplers.The transfer functions can be expressed as(10)H1,2=Zint2ZM1+ZM2+Zint2,(11)H1,2=Zint2ZM1+ZM2+Zint2.By solving Equations (3)–(11), the component value in the π model can be obtained:
(12)ZM=Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z14Z23Z24Z14Z23−Z13Z24,Zint1=Z12Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z14Z23Z24Z12Z13Z23+2Z12Z13Z24+Z12Z14Z24+Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z14Z23Z24,Zint2=Z34Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z14Z23Z24Z13Z14Z23+Z13Z14Z24+Z13Z23Z24+Z13Z14Z34+Z14Z23Z24+2Z13Z24Z34+Z23Z24Z34,where ZM=ZM1+ZM2.


## 3. Capacitive Data Transfer System Based on Push-Pull Inverter

In this section, the top to down system design is elaborated. The load shift keying circuitry is firstly presented to illustrate the effect of the load change on the underground coupler impedance. Then, the mechanism of the push-pull inverter is briefly discussed, and modifications have been made to improve the design. The proposed system design is verified by simulations using MATLAB Simulink.


### 3.1. Load Shift Keying (LSK) Circuitry

The diagram of LSK circuitry is shown in Figure5. The microcontroller inside the sensor unit collects the data and controls the MOSFET switch. The high and low signal states of the data can be represented by the open and closed states of the switch, respectively. When the switch is closed, plate 3 and plate 4 are connected. In this case, the secondary side is shorted, and the primary side can observe minimum impedance. Similarly, when the switch is in off-state, the maximum impedance occurs. The signal strength can be quantified as the percentage change in impedance between these two states. The maximum and minimum impedance can be derived as
(13)Zmax=Zint1ZM1+Zint2+ZM2,Zmin=Zint1ZM1+ZM2.Figure 5
Load shift keying (LSK) circuitry.Hence, the percentage of impedance change can be obtained as(14)ΔZ=Zmax−ZminZmin×100%=Zin,priZin,secZM1+ZM2ZM1+ZM2+Zin,pri+Zin,sec.The simulation has been conducted in CST to visualize the electric field distributions as well as to calculate the impedance. As shown in Figure6, the top two round metal plates are placed on the surface. The voltage difference (V1) is set to 1 V. The bottom two plates are buried in the soil. It can be seen that under the short-circuited scenario and open-circuited scenario, the electric field distributions are different. When the secondary side is shorted, the electric field gets attracted to the secondary plates, and the field strength between the secondary plates becomes weaker. A probe is inserted to measure the input current (I1) and the secondary plate voltage difference (V2). The input impedance Zin can then be calculated as Zin=V1/I1. The simulation results are summarized in Table 2.Figure 6
E-field distribution with short-circuit and open-circuit.Table 2
Measurements from CST simulations.
V1 (V)V2 (V)H1,2I1 (mA)Zin (Ω)Short-circuit10.030.030.25423930Open-circuit10.030.030.25423933It could be found that under short-circuit condition and open-circuit conditions, the observed input impedance has a small difference. With proper filter designs, the difference can be amplified to a detectable level.


### 3.2. Push-Pull Transformer FSK System

#### 3.2.1. Push-Pull Circuit Modelling

The autonomous push-pull inverter was firstly introduced by Hu and Abdolkhani [22]. It converts a DC voltage source into a high-frequency AC source. Compared to other inverter topologies, this topology has significant advantages for its simplicity and high efficiency. The push-pull inverter can always ensure soft-switching during the operation, minimizing the switching loss of the transistors and electromagnetic interference (EMI). In Figure 7, it shows a CPT system with the autonomous push-pull converter. The controller does not require any external controllers and makes it more economical to use.Figure 7
CPT system based on the improved autonomous push-pull inverter.The operation frequency of the autonomous push-pull controller is determined by the resonant componentsLr and Cr in the parallel tank. When the system is operating under the design frequency, it has the following relationship:
(15)ω=1LrCr=1LsCs,where Cs is the equivalent coupling capacitance, Cs=Cs1Cs2/Cs1+Cs2.The operation frequency of the push-pull inverter can be easily affected by the load. If the load has the capacitive component, the operation frequency will be lower than the designed value. Meanwhile, if the load has the inductive component, the operation frequency will be higher. The load impedance change caused by the LSK circuitry will lead to two different operation frequencies. By this unique feature, the high state and the low states of the data can then be expressed as the conditions of the switch.The performance of the autonomous push-pull converter is limited by its output voltage. Without additional circuits, the output voltage across the parallel resonant tank is bounded byπVDC. A transformer is used to level up the voltage. As depicted in Figure 8, the Tee model of the transformer is applied to analyze the circuit. The magnetization inductance LM can be used to replace the resonant inductor Lr to further reduce the converter size.Figure 8
Simplified circuit diagram for a push-pull inverter with a nonideal transformer.As the system is running at the megahertz region, the nonideal properties of the transformer also need to be considered. The leakage inductance on the primary side and secondary side is described asL11 and L22, respectively. Additional capacitor CT is used to compensate the leakage inductance L22 to achieve maximum sensitivity. In other words, the operation frequency of the push-pull inverter will only vary when the load impedance changes. No compensation is needed for L11 as the step-up transformer has a much lower primary inductance compared to L22.The simulation model has been structured using the MATLAB Simscape package as shown in Figure9. The transformer is set to have a turn ratio α=3 with a coupling factor kc of 0.8. The MOSFET parameters are imported from nominal values of a fast-switching MOSFET, IRF510. A square wave signal is applied to the switch to mimic the data transfer. Detailed simulation parameters are attached in Table 3.Figure 9
MATLAB simulation model.Table 3
Simulation parameters.
ParameterValuesParameterValuesL1,L2680 μHR1,R2150 ΩC1,C2140 pFkc0.8LT,p30μHLT,s270μHCr500 pFCT367 pFVDC6 Vα3As shown in Figure10(b), the output voltage of the push-pull inverter has an amplitude of around 18.5 V, which is close to πVDC. After the transformer, the voltage is boosted up to 52.5 V. The voltage gain is close to the designed turns ratio. It can also be seen from Figure 10(d) that when the switching signal is applied, the operation frequency can change slightly from 1.082 MHz to 1.086 MHz.Figure 10
Simulation results.
(a)
Output voltage of the push-pull inverter(b)
Boosted voltage after the transformer(c)
Switching signal(d)
Resulting frequency variation


#### 3.2.2. System Design

As discussed above, the operation frequency of the push-pull inverter will change automatically when the observed impedance changes. This paper utilizes this feature and designs an FSK demodulator based on Phase Lock Loop (PLL). Figure11 illustrates the overall system diagram.Figure 11
CPT data transfer system based on push-pull inverter.An extra winding is firstly used on the transformer to step down the push-pull inverter output voltage to a detectable analogue voltage. This lowered voltage is fed into the phase comparator and compared with the signal generated by the voltage-controlled oscillator (VCO). The phase comparator output signal will then be filtered. As the input analogue voltage frequency changes, the amplitude of this signal will vary correspondingly. The variations are captured and recovered to the data using cascaded filters and processed by a programmable system-on-chip (PSoC).


## 3.1. Load Shift Keying (LSK) Circuitry

The diagram of LSK circuitry is shown in Figure5. The microcontroller inside the sensor unit collects the data and controls the MOSFET switch. The high and low signal states of the data can be represented by the open and closed states of the switch, respectively. When the switch is closed, plate 3 and plate 4 are connected. In this case, the secondary side is shorted, and the primary side can observe minimum impedance. Similarly, when the switch is in off-state, the maximum impedance occurs. The signal strength can be quantified as the percentage change in impedance between these two states. The maximum and minimum impedance can be derived as
(13)Zmax=Zint1ZM1+Zint2+ZM2,Zmin=Zint1ZM1+ZM2.Figure 5
Load shift keying (LSK) circuitry.Hence, the percentage of impedance change can be obtained as(14)ΔZ=Zmax−ZminZmin×100%=Zin,priZin,secZM1+ZM2ZM1+ZM2+Zin,pri+Zin,sec.The simulation has been conducted in CST to visualize the electric field distributions as well as to calculate the impedance. As shown in Figure6, the top two round metal plates are placed on the surface. The voltage difference (V1) is set to 1 V. The bottom two plates are buried in the soil. It can be seen that under the short-circuited scenario and open-circuited scenario, the electric field distributions are different. When the secondary side is shorted, the electric field gets attracted to the secondary plates, and the field strength between the secondary plates becomes weaker. A probe is inserted to measure the input current (I1) and the secondary plate voltage difference (V2). The input impedance Zin can then be calculated as Zin=V1/I1. The simulation results are summarized in Table 2.Figure 6
E-field distribution with short-circuit and open-circuit.Table 2
Measurements from CST simulations.
V1 (V)V2 (V)H1,2I1 (mA)Zin (Ω)Short-circuit10.030.030.25423930Open-circuit10.030.030.25423933It could be found that under short-circuit condition and open-circuit conditions, the observed input impedance has a small difference. With proper filter designs, the difference can be amplified to a detectable level.


## 3.2. Push-Pull Transformer FSK System

### 3.2.1. Push-Pull Circuit Modelling

The autonomous push-pull inverter was firstly introduced by Hu and Abdolkhani [22]. It converts a DC voltage source into a high-frequency AC source. Compared to other inverter topologies, this topology has significant advantages for its simplicity and high efficiency. The push-pull inverter can always ensure soft-switching during the operation, minimizing the switching loss of the transistors and electromagnetic interference (EMI). In Figure 7, it shows a CPT system with the autonomous push-pull converter. The controller does not require any external controllers and makes it more economical to use.Figure 7
CPT system based on the improved autonomous push-pull inverter.The operation frequency of the autonomous push-pull controller is determined by the resonant componentsLr and Cr in the parallel tank. When the system is operating under the design frequency, it has the following relationship:
(15)ω=1LrCr=1LsCs,where Cs is the equivalent coupling capacitance, Cs=Cs1Cs2/Cs1+Cs2.The operation frequency of the push-pull inverter can be easily affected by the load. If the load has the capacitive component, the operation frequency will be lower than the designed value. Meanwhile, if the load has the inductive component, the operation frequency will be higher. The load impedance change caused by the LSK circuitry will lead to two different operation frequencies. By this unique feature, the high state and the low states of the data can then be expressed as the conditions of the switch.The performance of the autonomous push-pull converter is limited by its output voltage. Without additional circuits, the output voltage across the parallel resonant tank is bounded byπVDC. A transformer is used to level up the voltage. As depicted in Figure 8, the Tee model of the transformer is applied to analyze the circuit. The magnetization inductance LM can be used to replace the resonant inductor Lr to further reduce the converter size.Figure 8
Simplified circuit diagram for a push-pull inverter with a nonideal transformer.As the system is running at the megahertz region, the nonideal properties of the transformer also need to be considered. The leakage inductance on the primary side and secondary side is described asL11 and L22, respectively. Additional capacitor CT is used to compensate the leakage inductance L22 to achieve maximum sensitivity. In other words, the operation frequency of the push-pull inverter will only vary when the load impedance changes. No compensation is needed for L11 as the step-up transformer has a much lower primary inductance compared to L22.The simulation model has been structured using the MATLAB Simscape package as shown in Figure9. The transformer is set to have a turn ratio α=3 with a coupling factor kc of 0.8. The MOSFET parameters are imported from nominal values of a fast-switching MOSFET, IRF510. A square wave signal is applied to the switch to mimic the data transfer. Detailed simulation parameters are attached in Table 3.Figure 9
MATLAB simulation model.Table 3
Simulation parameters.
ParameterValuesParameterValuesL1,L2680 μHR1,R2150 ΩC1,C2140 pFkc0.8LT,p30μHLT,s270μHCr500 pFCT367 pFVDC6 Vα3As shown in Figure10(b), the output voltage of the push-pull inverter has an amplitude of around 18.5 V, which is close to πVDC. After the transformer, the voltage is boosted up to 52.5 V. The voltage gain is close to the designed turns ratio. It can also be seen from Figure 10(d) that when the switching signal is applied, the operation frequency can change slightly from 1.082 MHz to 1.086 MHz.Figure 10
Simulation results.
(a)
Output voltage of the push-pull inverter(b)
Boosted voltage after the transformer(c)
Switching signal(d)
Resulting frequency variation


### 3.2.2. System Design

As discussed above, the operation frequency of the push-pull inverter will change automatically when the observed impedance changes. This paper utilizes this feature and designs an FSK demodulator based on Phase Lock Loop (PLL). Figure11 illustrates the overall system diagram.Figure 11
CPT data transfer system based on push-pull inverter.An extra winding is firstly used on the transformer to step down the push-pull inverter output voltage to a detectable analogue voltage. This lowered voltage is fed into the phase comparator and compared with the signal generated by the voltage-controlled oscillator (VCO). The phase comparator output signal will then be filtered. As the input analogue voltage frequency changes, the amplitude of this signal will vary correspondingly. The variations are captured and recovered to the data using cascaded filters and processed by a programmable system-on-chip (PSoC).


## 3.2.1. Push-Pull Circuit Modelling

The autonomous push-pull inverter was firstly introduced by Hu and Abdolkhani [22]. It converts a DC voltage source into a high-frequency AC source. Compared to other inverter topologies, this topology has significant advantages for its simplicity and high efficiency. The push-pull inverter can always ensure soft-switching during the operation, minimizing the switching loss of the transistors and electromagnetic interference (EMI). In Figure 7, it shows a CPT system with the autonomous push-pull converter. The controller does not require any external controllers and makes it more economical to use.Figure 7
CPT system based on the improved autonomous push-pull inverter.The operation frequency of the autonomous push-pull controller is determined by the resonant componentsLr and Cr in the parallel tank. When the system is operating under the design frequency, it has the following relationship:
(15)ω=1LrCr=1LsCs,where Cs is the equivalent coupling capacitance, Cs=Cs1Cs2/Cs1+Cs2.The operation frequency of the push-pull inverter can be easily affected by the load. If the load has the capacitive component, the operation frequency will be lower than the designed value. Meanwhile, if the load has the inductive component, the operation frequency will be higher. The load impedance change caused by the LSK circuitry will lead to two different operation frequencies. By this unique feature, the high state and the low states of the data can then be expressed as the conditions of the switch.The performance of the autonomous push-pull converter is limited by its output voltage. Without additional circuits, the output voltage across the parallel resonant tank is bounded byπVDC. A transformer is used to level up the voltage. As depicted in Figure 8, the Tee model of the transformer is applied to analyze the circuit. The magnetization inductance LM can be used to replace the resonant inductor Lr to further reduce the converter size.Figure 8
Simplified circuit diagram for a push-pull inverter with a nonideal transformer.As the system is running at the megahertz region, the nonideal properties of the transformer also need to be considered. The leakage inductance on the primary side and secondary side is described asL11 and L22, respectively. Additional capacitor CT is used to compensate the leakage inductance L22 to achieve maximum sensitivity. In other words, the operation frequency of the push-pull inverter will only vary when the load impedance changes. No compensation is needed for L11 as the step-up transformer has a much lower primary inductance compared to L22.The simulation model has been structured using the MATLAB Simscape package as shown in Figure9. The transformer is set to have a turn ratio α=3 with a coupling factor kc of 0.8. The MOSFET parameters are imported from nominal values of a fast-switching MOSFET, IRF510. A square wave signal is applied to the switch to mimic the data transfer. Detailed simulation parameters are attached in Table 3.Figure 9
MATLAB simulation model.Table 3
Simulation parameters.
ParameterValuesParameterValuesL1,L2680 μHR1,R2150 ΩC1,C2140 pFkc0.8LT,p30μHLT,s270μHCr500 pFCT367 pFVDC6 Vα3As shown in Figure10(b), the output voltage of the push-pull inverter has an amplitude of around 18.5 V, which is close to πVDC. After the transformer, the voltage is boosted up to 52.5 V. The voltage gain is close to the designed turns ratio. It can also be seen from Figure 10(d) that when the switching signal is applied, the operation frequency can change slightly from 1.082 MHz to 1.086 MHz.Figure 10
Simulation results.
(a)
Output voltage of the push-pull inverter(b)
Boosted voltage after the transformer(c)
Switching signal(d)
Resulting frequency variation


## 3.2.2. System Design

As discussed above, the operation frequency of the push-pull inverter will change automatically when the observed impedance changes. This paper utilizes this feature and designs an FSK demodulator based on Phase Lock Loop (PLL). Figure11 illustrates the overall system diagram.Figure 11
CPT data transfer system based on push-pull inverter.An extra winding is firstly used on the transformer to step down the push-pull inverter output voltage to a detectable analogue voltage. This lowered voltage is fed into the phase comparator and compared with the signal generated by the voltage-controlled oscillator (VCO). The phase comparator output signal will then be filtered. As the input analogue voltage frequency changes, the amplitude of this signal will vary correspondingly. The variations are captured and recovered to the data using cascaded filters and processed by a programmable system-on-chip (PSoC).


## 4. Experimental Results

Figure12 shows the experiment setup. A 70-litre container filled with soils is used to simulate the ground condition. On the left side, the sensor unit uses a STM32 microcontroller to transmit data continuously, powered by a 9 V battery. On the right side, the push-pull inverter is connected with an auxiliary power supply. A probe is connected to monitor the VCO input voltage. The voltage signal is also fed into a PSoC5 microcontroller to convert back into a UART data string and displayed on a PC screen. The baud rate is set to 9600.Figure 12
Experiment setup.All component values are included in Table4. The leakage inductance of the transformer properties is preverified by undertaking short-circuit and open-circuit tests under the operation frequency of 1 MHz. It should be noted that the value of Cr is smaller than the one used in the simulation. This is because the output capacitance of the MOSFETs contributes to Cr as well.Table 4
Experiment component parameters.
ParameterValuesParameterValuesL1,L2680μHR1,R2150ΩC1,C2140 pFkc0.8LT,p30μHLT,s270μHCr243 pFCT330 pFVDC6 Vα3PLLCD4046BEMOSFETIRF510The experiments were conducted under the configuration shown in Figure1. In the setup, we assume that the longitudinal distance lpp=lss=12cm; thus, lmis is equal to 0. The lateral distance lps=12 cm.As shown in Figure13, the VCO output voltage was captured with native Keysight desktop application. After filtering the signal, the emulator application “PuTTY” was able to recognise the signal and converted into original data. The data was sent at a baud rate of 9600 in every 0.5 s, and the system was able to run continuously over a long time.Figure 13
Data transmission experiment.The signal strength was measured in terms of the AC signal amplitude. With a fixed longitudinal distance, multiple testings have been conducted to test the maximum lateral transmission distance. As shown in Figure14, all signal strength curves follow an exponential decay. With an increasing lateral distance, the voltage differences drop dramatically and become much harder to detect.Figure 14
Signal strength under different lateral distances.
(a)
lpp=lss=14cm(b)
lpp=lss=16cm(c)
lpp=lss=18cm(d)
lpp=lss=20cmSimilar testings have also been conducted to find the maximum longitudinal distance. The results are illustrated in Figure15. During the experiments, the maximum data transfer range is found around 1.2lps with no bit error rate (BER). It should be noticed that under that same lateral distance, the voltage difference will be more significant with a longer longitudinal distance. Less electric fields are attracted to the horizontal plate, resulting in a smaller cross-coupling capacitance between the two primary plates. To get a further transmission range, the two primary plates should be placed as far as possible.Figure 15
Signal strength under different longitudinal distances.Additional testings have been carried out to explore the performance of this data transfer system under different soil moisture levels, as shown in Figure16. It can be found that with the dry soils, the signal strength is the strongest. The signal strength will drop significantly as the water concentration increases. This phenomenon agrees with the studies in [3]. A higher moisture level in soils will cause additional path loss during the data transmission.Figure 16
Signal strength under different soil moisture levels.


## 5. Conclusion

This paper explores the feasibility of applying capacitive power transfer technology (CPT) in an underground data transfer system. The differences of using air and soils as the medium of couplers have been explained and visualized. We have extended the current air coupler model to a more generalized expression to describe the electrical properties of soils. The push-pull inverter has been chosen to drive the CPT system, on which a transformer has been employed to increase the data transmission range. By introducing an LSK circuitry to control a switch on the sensor side, the observed load impedance will change correspondingly, leading to operation frequency variations. These variations are captured by the FSK circuitry on the receiving end and demodulated. The prototype has been implemented and tested in various working conditions. The proposed design has been proved valid and successful.



---

*Source: 8849618-2020-09-15.xml*