# Experiment on Bifurcation and Chaos in Coupled Anisochronous Self-Excited Systems: Case of Two Coupled van der Pol-Duffing Oscillators

Authors: J. Kengne; F. Kenmogne; V. Kamdoum Tamba
Journal: Journal of Nonlinear Dynamics
 (2014)

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## Abstract

The analog circuit implementation and the experimental bifurcation analysis of coupled anisochronous self-driven systems modelled by two mutually coupled van der Pol-Duffing oscillators are considered. The coupling between the two oscillators is set in a symmetrical way that linearly depends on the difference of their velocities (i.e., dissipative coupling). Interest in this problem does not decrease because of its significance and possible application in the analysis of different, biological,  chemical, and electrical systems (e.g., coupled van der Pol-Duffing electrical system). Regions of quenching behavior as well as conditions for the appearance of Hopf bifurcations are analytically defined. The scenarios/routes to chaos are studied with particular emphasis on the effects of cubic nonlinearity (that is responsible for anisochronism of small oscillations). When monitoring the control parameter, various striking dynamic behaviors are found including period-doubling, symmetry-breaking, multistability, and chaos. An appropriate electronic circuit describing the coupled oscillator is designed and used for the investigations. Experimental results that are consistent with results from theoretical analyses are presented and convincingly show quenching phenomenon as well as bifurcation and chaos.


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## Body

## 1. Introduction

In recent years, considerable research efforts had been devoted to the analysis of coupled limit-cycle oscillators models due to the useful insight they provide into the collective dynamics of various physical, biological, chemical, and electrical (e.g., coupled van der Pol-Duffing electrical circuit) systems [1–5]. The system of two coupled van der Pol oscillators is one of the canonical models exhibiting the mutual synchronisation behaviour [6]. Coupled self-oscillators demonstrate some classical effects such as phase locking of the oscillations with different ratios of the frequencies [7]. Amplitude death or quenching is possible in case of dissipative coupling [8, 9]. This phenomenon has been observed experimentally in the system of coupled electromechanical oscillators [10], coupled electronic systems [11], and coupled biological oscillators [11] just to name a few. Multistability, chaos, and nonisochronism are some special effects of the synchronization picture presented by researchers [12–17].Introducing additional nonlinearity of Duffing type in the original van der Pol equation leads to the so-called van der Pol-Duffing equation for which potential contains a component in the form of the coordinate raised to the fourth power [18–20]. This component models an interesting physical effect, namely, an opportunity of anisochronous oscillations, defined as the dependence of oscillation frequency on oscillation amplitude. Using the method of dynamic regime chart, the specific properties of synchronization for coupled autooscillating systems characterized by nonquadratic law of potential dependence on the coordinate were discussed in [18]. For the special case of mutually coupled van der Pol-Duffing oscillators, the structure of the parameter plane (frequency mismatch-coupling strength) was presented. The features of attractors in phase space were examined as well as the arrangement of synchronization tongues and corresponding internal structure in the parameter space. Regions of amplitude death behaviour were also depicted. However the important role of the anisochronism parameter/coefficient (i.e., the cubic nonlinearity parameter of the model) was not sufficiently highlighted. Furthermore, no tractable analytical formulae were provided to define regions of the parameters space corresponding to specific type of behaviours (e.g., Hopf bifurcation, amplitude death, and so on). Also, in order to show the reader the validity of the numerically observed phenomena related to oscillation quenching and bifurcation to chaos of two coupled van der Pol-Duffing oscillators, full-scale experiment with electronic circuits [6] would have been welcomed. With the motivation of shedding more light on the dynamics of such a coupled system, our objective in this paper is threefold: (i) to consider the dynamics of the coupled oscillators and define (analytically) regions of parameters space corresponding to the quenching mode of oscillations; (ii) to investigate the bifurcation structures of the system with particular attention on the effects of anisochronism; (iii) to carry out an experimental study of the system to validate and complement the theoretical results.The paper is structured as follows. Section2 describes the mathematical model of the system under investigation and underlines possible symmetries. The coupled van der Pol-Duffing electrical circuit is presented as a prototypal anisochronous self-excited system. In Section 3, conditions for oscillation death behaviour are derived as well as those related to the occurrence of Hopf bifurcations. Section 4 investigates the bifurcation structures of the system numerically with particular emphasis on the effects of cubic nonlinearity of the model. In Section 5, an appropriate analog computer is proposed for the analysis of the dynamic behaviour of the coupled system. Correspondences are established between the coefficients of the system model and the components of the analog simulator. Experimental and numerical results are compared. Some concluding remarks are presented in Section 6.


## 2. System Model

### 2.1. Description and Analysis of the Model

The dynamics of a system consisting of two mutually coupled van der Pol-Duffing oscillators considered in this work is described by the following set of equations:(1a)x¨-(ε-x2)x˙+x+βx3-μ(y˙-x˙)=0,(1b)y¨-(ε-y2)y˙+(1+Δ)y+βy3-μ(x˙-y˙)=0,where Δ is the frequency mismatch between the second and the first oscillators and ε characterizes the excess above the threshold of Andronov-Hopf bifurcation in autonomous oscillators [18], while μ represents the coupling strength. The parameter β (β≥0) defines the perturbation quantity of the quadratic (single-well) potential and consequently is responsible for anisochronism of small oscillations. Setting x˙=u and y˙=v, system (1a) and (1b) can be rewritten as a set of four first-order differential equations in the form(2a)x˙=u,(2b)u˙=(ε-x2)u-x-βx3+μ(v-u),(2c)y˙=v,(2d)v˙=(ε-y2)v-(1+Δ)y-βy3+μ(u-v).For μ=0, both oscillators are uncoupled and each exhibits a limit cycle attractor. Obviously the coupling employed is a linear feedback which can be viewed as the perturbation of each oscillator by a signal proportional to the difference of their velocities (i.e., dissipative coupling). We note that system (2a)–(2d) is invariant under the transformation:
(3)(x(t),u(t),y(t),v(t))⟺(-x(t),-u(t),-y(t),-v(t)).
Therefore, if (x(t),u(t),y(t),v(t)) is a solution of system (2a)–(2d) for a specific set of parameters ε, μ, Δ, and β, then (-x(t),-u(t),-y(t),-v(t)) is also a solution for the same parameters set. The fixed point O(0,0,0,0) is a trivial symmetric solution. Consequently, attractors in state space have to be symmetric with respect to the origin; otherwise they must appear in pairs, to restore the exact symmetry of the model equations. This exact symmetry may serve to explain the existence of several attractors in state space.


### 2.2. Example of Coupled Anisochronous Self-Excited System

As a prototypal dynamic system (related to the model defined in (1a) and (1b)), we consider the coupled van der Pol-Duffing electrical circuit depicted in Figure 1. The coupled system consists of two oscillators X (Figure 1(a)) and Y (Figure 1(b)) interconnected via a coupling module (Figure 1(c)). The set of diodes Dj(j=1-8) with related op. amplifier is the physical implementation of the nonlinear element/resistor responsible for the complex behavior observed in the coupled system. The current-voltage (I-V) characteristic of this nonlinear resistor [5] can be approximated by a cubic polynomial I(V)=-aV+bV3 (a,b>0). The coupling module involves a differential voltage amplifier followed by an inverter stage. In each oscillator stage, a current to voltage converter is series inserted with the capacitor to obtain the input signal for the coupling module. Denoting by V1 and V2 the voltage across capacitor C involved in the Van der Pol-Duffing oscillators X and Y, respectively, the application of Kirchhoff current and voltage laws to the schematic diagram of Figure 1 leads to the derivation of the following differential equations describing the coupled system: (4a)LCd2V1dτ2+[R1AC+L(-a+3bV12)]dV1dτ+(-aR1A+1)V1+R1bV13+AdRfC(dV1dτ-dV2dτ)=0,(4b)LCd2V2dτ2+[R1BC+L(-a+3bV22)]dV2dτ+(-aR1B+1)V2+R1BbV23+AdRfC(dV2dτ-dV1dτ)=0,where Ad represents the gain of the differential amplifier stage (see Figure 1 caption). With the following change of variables and parameters:
(5)τ=tLC,ρ=LC,μ=AdRfρ,Vref=13bρ,ω12=1-aR1A,ω22=1-aR1B,ε1=aρ-R1Aρ,ε2=aρ-R1Bρ,ρ=LC,β1=R1AbVref2,β2=R1BbVref2,x=V1Vref,y=V2Vref,
the nondimensional circuit equation can be rewritten as follows:(6a)x¨-(ε1-x2)x˙+ω12x+β1x3-μ(y˙-x˙)=0,(6b)y¨-(ε2-y2)y˙+ω22y+β2y3-μ(x˙-y˙)=0,where the dot denotes the derivation with respect to the nondimensional time t. System (6a) and (6b) shows that the mathematical model describing the coupled van der Pol-Duffing electrical circuit is similar to the model defined in (1a) and (1b). Thus our motivation in this work is to carry out an abstract study of the system evolution (1a) and (1b); thereafter, the results obtained can be exploited as predictions for the physical system.Scheme of a pair of coupled van der Pol-Duffing electrical system: (a) oscillator X, (b) oscillatorY, and (c) coupling module. The relationships between the coupling module’s components are R9=R10, R5=R7, R6=R8; thus we have Ad=R8/R7.
(a)
(b)
(c)


## 2.1. Description and Analysis of the Model

The dynamics of a system consisting of two mutually coupled van der Pol-Duffing oscillators considered in this work is described by the following set of equations:(1a)x¨-(ε-x2)x˙+x+βx3-μ(y˙-x˙)=0,(1b)y¨-(ε-y2)y˙+(1+Δ)y+βy3-μ(x˙-y˙)=0,where Δ is the frequency mismatch between the second and the first oscillators and ε characterizes the excess above the threshold of Andronov-Hopf bifurcation in autonomous oscillators [18], while μ represents the coupling strength. The parameter β (β≥0) defines the perturbation quantity of the quadratic (single-well) potential and consequently is responsible for anisochronism of small oscillations. Setting x˙=u and y˙=v, system (1a) and (1b) can be rewritten as a set of four first-order differential equations in the form(2a)x˙=u,(2b)u˙=(ε-x2)u-x-βx3+μ(v-u),(2c)y˙=v,(2d)v˙=(ε-y2)v-(1+Δ)y-βy3+μ(u-v).For μ=0, both oscillators are uncoupled and each exhibits a limit cycle attractor. Obviously the coupling employed is a linear feedback which can be viewed as the perturbation of each oscillator by a signal proportional to the difference of their velocities (i.e., dissipative coupling). We note that system (2a)–(2d) is invariant under the transformation:
(3)(x(t),u(t),y(t),v(t))⟺(-x(t),-u(t),-y(t),-v(t)).
Therefore, if (x(t),u(t),y(t),v(t)) is a solution of system (2a)–(2d) for a specific set of parameters ε, μ, Δ, and β, then (-x(t),-u(t),-y(t),-v(t)) is also a solution for the same parameters set. The fixed point O(0,0,0,0) is a trivial symmetric solution. Consequently, attractors in state space have to be symmetric with respect to the origin; otherwise they must appear in pairs, to restore the exact symmetry of the model equations. This exact symmetry may serve to explain the existence of several attractors in state space.


## 2.2. Example of Coupled Anisochronous Self-Excited System

As a prototypal dynamic system (related to the model defined in (1a) and (1b)), we consider the coupled van der Pol-Duffing electrical circuit depicted in Figure 1. The coupled system consists of two oscillators X (Figure 1(a)) and Y (Figure 1(b)) interconnected via a coupling module (Figure 1(c)). The set of diodes Dj(j=1-8) with related op. amplifier is the physical implementation of the nonlinear element/resistor responsible for the complex behavior observed in the coupled system. The current-voltage (I-V) characteristic of this nonlinear resistor [5] can be approximated by a cubic polynomial I(V)=-aV+bV3 (a,b>0). The coupling module involves a differential voltage amplifier followed by an inverter stage. In each oscillator stage, a current to voltage converter is series inserted with the capacitor to obtain the input signal for the coupling module. Denoting by V1 and V2 the voltage across capacitor C involved in the Van der Pol-Duffing oscillators X and Y, respectively, the application of Kirchhoff current and voltage laws to the schematic diagram of Figure 1 leads to the derivation of the following differential equations describing the coupled system: (4a)LCd2V1dτ2+[R1AC+L(-a+3bV12)]dV1dτ+(-aR1A+1)V1+R1bV13+AdRfC(dV1dτ-dV2dτ)=0,(4b)LCd2V2dτ2+[R1BC+L(-a+3bV22)]dV2dτ+(-aR1B+1)V2+R1BbV23+AdRfC(dV2dτ-dV1dτ)=0,where Ad represents the gain of the differential amplifier stage (see Figure 1 caption). With the following change of variables and parameters:
(5)τ=tLC,ρ=LC,μ=AdRfρ,Vref=13bρ,ω12=1-aR1A,ω22=1-aR1B,ε1=aρ-R1Aρ,ε2=aρ-R1Bρ,ρ=LC,β1=R1AbVref2,β2=R1BbVref2,x=V1Vref,y=V2Vref,
the nondimensional circuit equation can be rewritten as follows:(6a)x¨-(ε1-x2)x˙+ω12x+β1x3-μ(y˙-x˙)=0,(6b)y¨-(ε2-y2)y˙+ω22y+β2y3-μ(x˙-y˙)=0,where the dot denotes the derivation with respect to the nondimensional time t. System (6a) and (6b) shows that the mathematical model describing the coupled van der Pol-Duffing electrical circuit is similar to the model defined in (1a) and (1b). Thus our motivation in this work is to carry out an abstract study of the system evolution (1a) and (1b); thereafter, the results obtained can be exploited as predictions for the physical system.Scheme of a pair of coupled van der Pol-Duffing electrical system: (a) oscillator X, (b) oscillatorY, and (c) coupling module. The relationships between the coupling module’s components are R9=R10, R5=R7, R6=R8; thus we have Ad=R8/R7.
(a)
(b)
(c)


## 3. Stability Analysis

### 3.1. Oscillation Quenching

In addition to the classical phase locking phenomenon, oscillation death also referred to as amplitude death or oscillation quenching is one of the most intriguing effects that can occur in mutually coupled limit cycle oscillators when, due to coupling, oscillations stop completely [6, 21, 22]. Two kinds of oscillation death are distinguished. In the first type, the coupling creates a saddle-node pair of fixed points on the limit cycle of the entrained oscillations, while the second type is associated with a classical Hopf bifurcation in which the oscillation amplitudes are damped out up to reach a stable equilibrium/fixed point [6, 21]. In this section, conditions for the occurrence of amplitude death behaviour are derived by examining the stability of the trivial equilibrium point (i.e., the origin O=(0,0,0,0)T) of the coupled system (2a)–(2d). In this regard, the Jacobian matrix evaluated at any equilibrium point (x0,u0,y0,v0)T can be easily computed as follows: (7)MJ=[0100-1-3βx02-2u0x0ε-μ-x020μ00010μ-1-Δ-3βy02-2v0y0ε-μ-y02].Thus the Jacobean matrix evaluated at the equilibrium point O(0,0,0,0)T satisfies the following characteristic equation (det⁡(MJ-λId)=0): (8a)λ4+c3λ3+c2λ2+c1λ+c0=0,
where
(8b)c0=1+Δ,c1=(2+Δ)(μ-ε),c2=ε2-2με+Δ+2,c3=2(μ-ε).A set of necessary and sufficient conditions for all the roots of (8a) and (8b)  to have negative real parts is given by the well-known Routh-Hurwitz criterion expressed in the form (9a)ci>0(i=0,1,2,3),(9b)c3c2-c1>0,(9c)c3(c1c2-c0c3)-c12>0.After some algebraic manipulations, the region of parameters space corresponding to the regime of oscillation death behaviour (i.e., stable equilibrium point) is defined by the following inequality: (10a)ε<μ<ε2+Δ24ε(2+Δ).
In addition, Δ must be greater than the critical value given by
(10b)Δc=ε2+ε4+ε2.If conditions (9a)–(9c) are not satisfied, the coupled system exhibits oscillatory motion; correspondingly the boundaries defined in (10a) and (10b)  may be associated with a Hopf bifurcation as will be discussed in the next section. Typical phase portrait and time traces related to a quenching state of the coupled system are provided in Figure 2.Time traces (a) and phase portraits (b) corresponding to a quenching behaviour of the mutually coupled van der Pol-Duffing oscillators. Amplitudes of both oscillators decay to zero as time evolves. The parameters areε=1.25; β=1.00; μ=1.50; Δ=10.
(a)
(b)


### 3.2. Hopf Bifurcation

The Hopf type bifurcations [23] are observed if the following conditions are fulfilled: (a) (8a) and (8b)  have a pair of pure imaginary complex eigenvalues λ1,2=±jω0=±j1+Δ/2; (b) the derivative of the real part of λ with respect to the control parameter must be different to zero when this control parameter approaches the critical value (i.e., dλ/dα|μ=μc≠0; μ is the bifurcation control parameter and μc is a solution of the equation Re(λ)=0). The derivative of the real part of λ versus the control parameter μ can be found from (8a) and reads Re(dλ/dμ)|μ=μc=ε(2+Δ)(μ-ε)/((μ-ε)2(4+2Δ)+ε2(ε-2μ)2). It is clear that this quantity is different to zero, since μ>ε provided that μ approaches the critical value μc=ε/2+Δ2/4ε(2+Δ) corresponding to the upper bound of inequality (10a). Note that the lower bound of the same inequality is associated with a degenerate Hopf bifurcation. Briefly recall that when the Hopf bifurcation occurs, the coupled system moves from the state of amplitude death to an oscillatory regime. For illustrating purposes, we provide in Figure 3 the time traces and phase portrait corresponding to a quasi-sinusoidal behavior of the system after the occurrence of the Hopf bifurcation. Furthermore, in order test the validity of our analytical results, system (2a)–(2d) is integrated numerically following the Runge-Kutta scheme and the local maxima of solutions (i.e., x(t) and y(t)) are plotted versus the coupling strength μ. The results presented in Figure 4 are consistent with the analytical formulas (i.e., (10a) and (10b)) proposed for the definition of the parameter space corresponding to the quenching of oscillations in the coupled system. Note that, with the parameters setting in Figure 4, no quenching phenomenon is observed for values of Δ lower than the critical value Δc=4.1981. Also note, from Figure 4, the increase of the quenching domain/zone with increasing Δ.Time traces (a) of the limit cycle (b) born after the Hopf bifurcation showing a quasi-sinusoidal behavior of the system. The parameters areε=1.25; β=0.50; μ=2.40; Δ=10.
(a)
(b)Amplitude death zone as a function of the coupling strengthμ for three different values of frequency detuning Δ: (a) no death zone is observed for Δ=1; (b) smaller death zone is observed for Δ=10; (c) larger death zone is observed for Δ=20. The rest of parameters are β=0.50; ε=1.25.
(a)
(b)
(c)


## 3.1. Oscillation Quenching

In addition to the classical phase locking phenomenon, oscillation death also referred to as amplitude death or oscillation quenching is one of the most intriguing effects that can occur in mutually coupled limit cycle oscillators when, due to coupling, oscillations stop completely [6, 21, 22]. Two kinds of oscillation death are distinguished. In the first type, the coupling creates a saddle-node pair of fixed points on the limit cycle of the entrained oscillations, while the second type is associated with a classical Hopf bifurcation in which the oscillation amplitudes are damped out up to reach a stable equilibrium/fixed point [6, 21]. In this section, conditions for the occurrence of amplitude death behaviour are derived by examining the stability of the trivial equilibrium point (i.e., the origin O=(0,0,0,0)T) of the coupled system (2a)–(2d). In this regard, the Jacobian matrix evaluated at any equilibrium point (x0,u0,y0,v0)T can be easily computed as follows: (7)MJ=[0100-1-3βx02-2u0x0ε-μ-x020μ00010μ-1-Δ-3βy02-2v0y0ε-μ-y02].Thus the Jacobean matrix evaluated at the equilibrium point O(0,0,0,0)T satisfies the following characteristic equation (det⁡(MJ-λId)=0): (8a)λ4+c3λ3+c2λ2+c1λ+c0=0,
where
(8b)c0=1+Δ,c1=(2+Δ)(μ-ε),c2=ε2-2με+Δ+2,c3=2(μ-ε).A set of necessary and sufficient conditions for all the roots of (8a) and (8b)  to have negative real parts is given by the well-known Routh-Hurwitz criterion expressed in the form (9a)ci>0(i=0,1,2,3),(9b)c3c2-c1>0,(9c)c3(c1c2-c0c3)-c12>0.After some algebraic manipulations, the region of parameters space corresponding to the regime of oscillation death behaviour (i.e., stable equilibrium point) is defined by the following inequality: (10a)ε<μ<ε2+Δ24ε(2+Δ).
In addition, Δ must be greater than the critical value given by
(10b)Δc=ε2+ε4+ε2.If conditions (9a)–(9c) are not satisfied, the coupled system exhibits oscillatory motion; correspondingly the boundaries defined in (10a) and (10b)  may be associated with a Hopf bifurcation as will be discussed in the next section. Typical phase portrait and time traces related to a quenching state of the coupled system are provided in Figure 2.Time traces (a) and phase portraits (b) corresponding to a quenching behaviour of the mutually coupled van der Pol-Duffing oscillators. Amplitudes of both oscillators decay to zero as time evolves. The parameters areε=1.25; β=1.00; μ=1.50; Δ=10.
(a)
(b)


## 3.2. Hopf Bifurcation

The Hopf type bifurcations [23] are observed if the following conditions are fulfilled: (a) (8a) and (8b)  have a pair of pure imaginary complex eigenvalues λ1,2=±jω0=±j1+Δ/2; (b) the derivative of the real part of λ with respect to the control parameter must be different to zero when this control parameter approaches the critical value (i.e., dλ/dα|μ=μc≠0; μ is the bifurcation control parameter and μc is a solution of the equation Re(λ)=0). The derivative of the real part of λ versus the control parameter μ can be found from (8a) and reads Re(dλ/dμ)|μ=μc=ε(2+Δ)(μ-ε)/((μ-ε)2(4+2Δ)+ε2(ε-2μ)2). It is clear that this quantity is different to zero, since μ>ε provided that μ approaches the critical value μc=ε/2+Δ2/4ε(2+Δ) corresponding to the upper bound of inequality (10a). Note that the lower bound of the same inequality is associated with a degenerate Hopf bifurcation. Briefly recall that when the Hopf bifurcation occurs, the coupled system moves from the state of amplitude death to an oscillatory regime. For illustrating purposes, we provide in Figure 3 the time traces and phase portrait corresponding to a quasi-sinusoidal behavior of the system after the occurrence of the Hopf bifurcation. Furthermore, in order test the validity of our analytical results, system (2a)–(2d) is integrated numerically following the Runge-Kutta scheme and the local maxima of solutions (i.e., x(t) and y(t)) are plotted versus the coupling strength μ. The results presented in Figure 4 are consistent with the analytical formulas (i.e., (10a) and (10b)) proposed for the definition of the parameter space corresponding to the quenching of oscillations in the coupled system. Note that, with the parameters setting in Figure 4, no quenching phenomenon is observed for values of Δ lower than the critical value Δc=4.1981. Also note, from Figure 4, the increase of the quenching domain/zone with increasing Δ.Time traces (a) of the limit cycle (b) born after the Hopf bifurcation showing a quasi-sinusoidal behavior of the system. The parameters areε=1.25; β=0.50; μ=2.40; Δ=10.
(a)
(b)Amplitude death zone as a function of the coupling strengthμ for three different values of frequency detuning Δ: (a) no death zone is observed for Δ=1; (b) smaller death zone is observed for Δ=10; (c) larger death zone is observed for Δ=20. The rest of parameters are β=0.50; ε=1.25.
(a)
(b)
(c)


## 4. Routes to Chaos

According to the results obtained by Kuznetsov and coworkers [18–20], the dynamics of the coupled van der Pol-Duffing system with respect to the parameters ε, μ, and Δ is well mastered. We now concentrate on the effects of the cubic nonlinearity (i.e., parameter β) on the dynamics of the system. For this purpose, system (2a)–(2d) is integrated numerically to reveal different scenarios/routes to chaos in our model using the classical fourth-order Runge-Kutta formulas. For each value of β, the system is integrated for a sufficiently long time and transient is discarded. The bifurcation diagrams are obtained by plotting the maxima of x(t) and y(t) in terms of the control parameter β. The integration time step is always kept Δt≤0.005 and computations are carried out using variables and constants parameters in extended mode. To evaluate the degree of chaos, we compute the largest numerical one dimensional (1D) Lyapunov exponent (LLE), (LLE>0 for chaotic states, LLE<0 for regular states) and draw the corresponding bifurcation diagram. The largest numerical one dimensional (1D) Lyapunov is expressed as
(11)LLE=limt→∞[(1t)ln⁡(d(t))]with(d(t)=δx2+δu2+δy2+δv2)
and computed from the variational equations obtained by perturbing the solutions of (2a)–(2d) as follows: x→x+δx, u→u+δu, y→y+δy, and v→v+δv with the help of the algorithm proposed by Wolf et al. in [24]. Sample results are shown in Figure 5 from which a very rich and striking dynamic behaviour can be seen when the bifurcation control parameter β is slowly monitored. The bifurcation structures include period-doubling, symmetry-breaking, and small windows of regularity in chaotic domains. Those bifurcation scenarios are perfectly traced by the Lyapunov spectra (see Figure 5). Typical phase portraits showing sample states of the coupled system are shown in Figure 6. The phase portraits of Figures 6(a)–6(d) correspond to regular states while the one shown in Figure 6(d) depicts a chaotic behavior of the system. Note that attractors in Figures 6(b) and 6(c) are asymmetric and correspondingly coexisting solutions are obtained by changing the initial conditions. This denotes the bistability property of the coupled system. Similarly, the extreme sensitivity of the coupled system with respect to the coupling constant μ is illustrated by the bifurcation diagrams provided in Figures 7(a) and 7(b). It is worth mentioning that the results obtained here complement previous work presented in the pioneering literature [18–20].Bifurcation diagram of the system showing the coordinatesx (a) and y (c) in terms of the control parameter β and the corresponding graph (c) of the largest 1D Lyapunov exponent (LLE). The rest of parameters are ε=2.50; μ=1.25; Δ=10.
(a)
(b)
(c)Numerical phase portraits of the coupled system showing typical dynamic states for (a) period-5 forβ=0.65; (b) period-3 for β=0.90; (c) period-6 for β=0.95; (d) chaos for β=1.05. The rest of parameters are those in Figure 5.
(a)
(b)
(c)
(d)One parameter bifurcation diagrams showing the coordinateX in the Poincare cross section versus the coupling constant μ for different values of β  (i.e., β=0.50 (a) and β=1.00 (b)). The rest of parameters are ε=2.50; Δ=10.
(a)
(b)


## 5. Analog Computation

The analog simulation method is a convenient strategy to scan the parameter range in order to find the proper parameter values for a numerical integration. In contrast to numerical computation, there is no need to wait for long transient times when performing an analog computation. This may serve to explain the increasing interest devoted to this type of implementation for the analysis of complex nonlinear systems [25–27]. The aim of this section is to design and implement an appropriate analog circuit/simulator for the analysis of the model defined by the set of (1a) and (1b) in order to verify and complement the theoretical results obtained previously. The scenarios/routes to chaos in the system are searched experimentally. Numerical and experimental phase portraits are compared.


### 5.1. Design of the Analog Simulator

Figure8 is a circuit diagram of the proposed electronic simulator. The electronic multipliers Mi(i=1,2,3,4,5,6) are the analog devices AD633JN versions of the AD633 four-quadrant voltage multiplier chips. They are used to implement the nonlinear terms of our model. The integrators are built by using operational amplifiers (TL084CN) with feedback capacitors while summations are obtained using operational amplifiers with feedback resistors and input resistors. Adopting an appropriate time scaling [25–27], the simulator outputs can directly be displayed on an oscilloscope by connecting the voltages to the X input and Y input. For the oscillator X (resp., Y) the phase portraits are obtained by feeding the output of U1C (resp., U5D) to the X input and that of U1A (resp., U5B) to the Y input. It can be shown that the voltages at x (output of U1C) and y (output of U5D) satisfy the set of coupled nonlinear differential equations (1a) and (1b). In terms of electronic circuit components, the parameters of (1a) and (1b) are expressed as follows: (12a)ε=1104R15C12=1104R25C22,(12b)β=11010R13R11C11C12=11010R23R21C21C22,(12c)μ=1104R17C12=1104R27C22,(12d)Δ+1=1108R26R21C21C22.These mathematical definitions take into account the following critical relationships between the values of resistors and capacitors: (13a)106R14C12=106R24C22=1,(13b)108R16R11C11C12=1.The time unit adopted is 10-4s. Mention that the time scaling process offers to the analog devices the possibility to operate under their bandwidth. Furthermore the time scaling offers the possibility to simulate the behaviour of the system at any given frequency by expressing the real time variable t versus the analog computation time variable τ(t=10-aτ) allowing the simulation frequency to be 10+a times less than the real frequency. Here, a is a positive integer depending on the values of resistors and capacitors involved in the analog simulation. The reader is referred to the work of Chedjou et al. [26] for the complete derivation procedure. The values of circuit’s components of the overall analog simulator are provided in Table 1. From (12a) and (12b), it is possible to control each system parameter by simply monitoring a single resistor or a pair of resistors simultaneously. For instance, Δ can be controlled with R26 and ε, β, μ with Rj5, Rj3, and Rj7(j=1,2), respectively. A photograph of the experimental analog simulator is shown in Figure 9.Table 1
Values of capacitors and resistors used in the overall electronic simulator.
Resistors (Ω), capacitors (nF)
Oscil.X(j=1)
Oscil.Y(j=2)
R
j
1
1
0
4
1
0
4
R
j
2
1
0
4
1
0
4
R
j
3
0
–
1
0
3
0
–
1
0
3
R
j
4
100
100
R
j
5
0
–
1
0
4
0
–
1
0
4
R
j
6
1
0
4
0
–
1
0
4
R
j
7
0
–
1
0
4
0
–
1
0
4
C
j
1
10
10
C
j
2
10
10
R
31
(
coupling
)
1
0
4
1
0
4Figure 8
Schematic diagram of the electronic simulator. The network built around op. amplifiers U1D and U5A is the coupling module while the upper and lower networks implement oscillatorsX and Y, respectively. The values of capacitors and resistors are those in Table 1.Figure 9
Photograph of the experimental analog simulator.


### 5.2. Quenching Phenomenon

In order to experimentally observe the quenching phenomenon in the coupled van der Pol-Duffing oscillators considered in present paper, the values of resistorR26 have been successively chosen as indicated in the first column of Table 2, leading to the following settings of parameter Δ: 7.5, 10, 15, and 20, respectively. As in Section 3, we also set the nonlinearity parameter to β=0.50 by choosing Rj3(j=1,2)=200Ω while the values of control resistors Rj5 are Rj5(j=1,2)=8kΩ leading to ε=1.25. For each value of R26, the pair of resistors Rj7 (i.e., parameter μ) is slowly monitored. The experiments indicate that when Rj7 varies inside the interval [Rj7min⁡,Rj7max⁡], the two coupled oscillators stop oscillating. This nonoscillating state is marked by the presence of a point on the oscilloscope screen in XY mode. The experimental values of the thresholds Rj7min⁡ and Rj7max⁡, inside which the quenching phenomenon is observed, are indicated in the two last columns of Table 2. Those values are well in agreement with theoretical ones presented in the second and third columns of the same table. It is important to stress that, for values of R26≥1942Ω, the system keeps oscillating (i.e., no quenching is observed) for any choice of the control resistors Rj7. This observation is also in agreement with the theoretical analysis (see Section 3) from which the predicted critical value of R26 under which the quenching phenomenon may occur is R26c=1923Ω.Table 2
Values of parameters of the system for quenching phenomena; subscriptj=1,2 for  oscillators X and Y, respectively; all resistors values are expressed in Ω.
Detuning resistor
Theoretical values ofRj7
Experimental values ofRj7
R
26
R
j
7
min
⁡
R
j
7
max
⁡
R
j
7
min
⁡
R
j
7
max
⁡
1176
5527
8
·
10
3
5530
8012
909
4362
8
·
10
3
4373
8004
625
3056
8
·
10
3
3065
7990
476
2346
8
·
10
3
2352
8015


### 5.3. Bifurcation and Chaos

We now focus on the experimental bifurcation study of the coupled van der Pol-Duffing system with the help of the electronic simulator. The effects of cubic nonlinearity (i.e., parameterβ) on the behavior of the coupled system are investigated by monitoring the pair of resistors Rj3(j=1,2) while keeping the rest of electronic components values constant (see Table 1). In this section, the values of control resistors are chosen as follows: R26=909Ω, Rj7(j=1,2)=4kΩ, and Rj7(j=1,2)=8kΩ. The choice of these values is justified by our wish to use the same sets of parameters for both numerical and experimental analyses (i.e., ε=2.50, μ=1.25, and Δ=10). When monitoring simultaneously the control resistors Rj3, it is found that the electronic simulator experiences a rich and striking dynamical behaviour. Some sample phase portraits obtained experimentally are shown in Figure 10. Note the similarity between the numerically computed phase portraits (see Figure 6) and the experimental ones. Furthermore, from Figure 10, one can see that the experimental circuit experiences the same bifurcation structures as those obtained numerically.Experimental results showing typical phase portraits of the coupled system: (a) period-5 forRj3=155Ω; (b) period-3 for Rj3=110Ω; (c) period-6 for Rj3=105Ω; (d) chaos for Rj3=95Ω. For all pictures displayed, the scales are x=1v/div⁡ and y=5v/div⁡.
(a)
(b)
(c)
(d)


## 5.1. Design of the Analog Simulator

Figure8 is a circuit diagram of the proposed electronic simulator. The electronic multipliers Mi(i=1,2,3,4,5,6) are the analog devices AD633JN versions of the AD633 four-quadrant voltage multiplier chips. They are used to implement the nonlinear terms of our model. The integrators are built by using operational amplifiers (TL084CN) with feedback capacitors while summations are obtained using operational amplifiers with feedback resistors and input resistors. Adopting an appropriate time scaling [25–27], the simulator outputs can directly be displayed on an oscilloscope by connecting the voltages to the X input and Y input. For the oscillator X (resp., Y) the phase portraits are obtained by feeding the output of U1C (resp., U5D) to the X input and that of U1A (resp., U5B) to the Y input. It can be shown that the voltages at x (output of U1C) and y (output of U5D) satisfy the set of coupled nonlinear differential equations (1a) and (1b). In terms of electronic circuit components, the parameters of (1a) and (1b) are expressed as follows: (12a)ε=1104R15C12=1104R25C22,(12b)β=11010R13R11C11C12=11010R23R21C21C22,(12c)μ=1104R17C12=1104R27C22,(12d)Δ+1=1108R26R21C21C22.These mathematical definitions take into account the following critical relationships between the values of resistors and capacitors: (13a)106R14C12=106R24C22=1,(13b)108R16R11C11C12=1.The time unit adopted is 10-4s. Mention that the time scaling process offers to the analog devices the possibility to operate under their bandwidth. Furthermore the time scaling offers the possibility to simulate the behaviour of the system at any given frequency by expressing the real time variable t versus the analog computation time variable τ(t=10-aτ) allowing the simulation frequency to be 10+a times less than the real frequency. Here, a is a positive integer depending on the values of resistors and capacitors involved in the analog simulation. The reader is referred to the work of Chedjou et al. [26] for the complete derivation procedure. The values of circuit’s components of the overall analog simulator are provided in Table 1. From (12a) and (12b), it is possible to control each system parameter by simply monitoring a single resistor or a pair of resistors simultaneously. For instance, Δ can be controlled with R26 and ε, β, μ with Rj5, Rj3, and Rj7(j=1,2), respectively. A photograph of the experimental analog simulator is shown in Figure 9.Table 1
Values of capacitors and resistors used in the overall electronic simulator.
Resistors (Ω), capacitors (nF)
Oscil.X(j=1)
Oscil.Y(j=2)
R
j
1
1
0
4
1
0
4
R
j
2
1
0
4
1
0
4
R
j
3
0
–
1
0
3
0
–
1
0
3
R
j
4
100
100
R
j
5
0
–
1
0
4
0
–
1
0
4
R
j
6
1
0
4
0
–
1
0
4
R
j
7
0
–
1
0
4
0
–
1
0
4
C
j
1
10
10
C
j
2
10
10
R
31
(
coupling
)
1
0
4
1
0
4Figure 8
Schematic diagram of the electronic simulator. The network built around op. amplifiers U1D and U5A is the coupling module while the upper and lower networks implement oscillatorsX and Y, respectively. The values of capacitors and resistors are those in Table 1.Figure 9
Photograph of the experimental analog simulator.


## 5.2. Quenching Phenomenon

In order to experimentally observe the quenching phenomenon in the coupled van der Pol-Duffing oscillators considered in present paper, the values of resistorR26 have been successively chosen as indicated in the first column of Table 2, leading to the following settings of parameter Δ: 7.5, 10, 15, and 20, respectively. As in Section 3, we also set the nonlinearity parameter to β=0.50 by choosing Rj3(j=1,2)=200Ω while the values of control resistors Rj5 are Rj5(j=1,2)=8kΩ leading to ε=1.25. For each value of R26, the pair of resistors Rj7 (i.e., parameter μ) is slowly monitored. The experiments indicate that when Rj7 varies inside the interval [Rj7min⁡,Rj7max⁡], the two coupled oscillators stop oscillating. This nonoscillating state is marked by the presence of a point on the oscilloscope screen in XY mode. The experimental values of the thresholds Rj7min⁡ and Rj7max⁡, inside which the quenching phenomenon is observed, are indicated in the two last columns of Table 2. Those values are well in agreement with theoretical ones presented in the second and third columns of the same table. It is important to stress that, for values of R26≥1942Ω, the system keeps oscillating (i.e., no quenching is observed) for any choice of the control resistors Rj7. This observation is also in agreement with the theoretical analysis (see Section 3) from which the predicted critical value of R26 under which the quenching phenomenon may occur is R26c=1923Ω.Table 2
Values of parameters of the system for quenching phenomena; subscriptj=1,2 for  oscillators X and Y, respectively; all resistors values are expressed in Ω.
Detuning resistor
Theoretical values ofRj7
Experimental values ofRj7
R
26
R
j
7
min
⁡
R
j
7
max
⁡
R
j
7
min
⁡
R
j
7
max
⁡
1176
5527
8
·
10
3
5530
8012
909
4362
8
·
10
3
4373
8004
625
3056
8
·
10
3
3065
7990
476
2346
8
·
10
3
2352
8015


## 5.3. Bifurcation and Chaos

We now focus on the experimental bifurcation study of the coupled van der Pol-Duffing system with the help of the electronic simulator. The effects of cubic nonlinearity (i.e., parameterβ) on the behavior of the coupled system are investigated by monitoring the pair of resistors Rj3(j=1,2) while keeping the rest of electronic components values constant (see Table 1). In this section, the values of control resistors are chosen as follows: R26=909Ω, Rj7(j=1,2)=4kΩ, and Rj7(j=1,2)=8kΩ. The choice of these values is justified by our wish to use the same sets of parameters for both numerical and experimental analyses (i.e., ε=2.50, μ=1.25, and Δ=10). When monitoring simultaneously the control resistors Rj3, it is found that the electronic simulator experiences a rich and striking dynamical behaviour. Some sample phase portraits obtained experimentally are shown in Figure 10. Note the similarity between the numerically computed phase portraits (see Figure 6) and the experimental ones. Furthermore, from Figure 10, one can see that the experimental circuit experiences the same bifurcation structures as those obtained numerically.Experimental results showing typical phase portraits of the coupled system: (a) period-5 forRj3=155Ω; (b) period-3 for Rj3=110Ω; (c) period-6 for Rj3=105Ω; (d) chaos for Rj3=95Ω. For all pictures displayed, the scales are x=1v/div⁡ and y=5v/div⁡.
(a)
(b)
(c)
(d)


## 6. Concluding Remarks

The main concern of this paper was to investigate the dynamics of two mutually coupled van der Pol-Duffing oscillators. Standard nonlinear dynamic tools including phase portraits, frequency spectra, Lyapunov exponent, and bifurcation diagrams were used as indicators of chaotic motion. We have found that the coupled system can experience a variety of bifurcations, namely, symmetry-breaking, period-doubling, crises, and Hopf bifurcation, when monitoring the cubic nonlinearity coefficient that accounts for the anisochronism of small oscillations. Furthermore, oscillation death behaviour as well as phase synchronization between the two oscillators was also examined. An appropriate analog simulator was constructed and employed for the investigations. Despite the tolerance on the values of electronic components and the imperfections of the op. amplifiers of the analog simulator, the experimental and theoretical results show a close agreement.An interesting question under consideration is the study of the effects of both elastic and dissipative coupling on the dynamics of the coupled van der Pol-Duffing oscillators for more generalization. Another interesting issue under consideration is the analysis of the effects of time delay on the dynamics and synchronization of the coupled anisochronous oscillators in spite of practical coupling conditions and possible applications.



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*Source: 815783-2014-10-29.xml*