# Computationally Efficient Angle and Polarization Estimation in the Presence of Multipath Propagation Using Dual-Polarization Vector Sensor Array

Authors: Weijian Si; Pinjiao Zhao; Zhiyu Qu; Liwei Wang
Journal: International Journal of Antennas and Propagation
 (2016)

---

## Abstract

This paper presents a computationally efficient angle and polarization estimation method for a mixture of uncorrelated and coherent sources using a dual-polarization vector sensor array. The uncorrelated sources are separated from the coherent sources on the basis of the modulus property of eigenvalues. The angles of the uncorrelated sources are estimated by employing rotational invariance and the associated polarization is obtained from the estimate of the uncorrelated array response matrix through elementwise division. For the distinguished coherent sources, two Hankel matrices are constructed from the elements of the estimated coherent array response matrix of each coherent group, from which two rotational-invariant submatrix pairs are extracted for estimating the coherent angles with a high precision. The least-square solution to the coherent polarization equation is derived for estimating the coherent polarization parameters. For each uncorrelated source and coherent group, the proposed method estimates the associated angle and polarization parameters separately, which avoids the need of 3D spectral search. In comparison with the existing methods, the simulation results show that the proposed method yields favorable performance in terms of computational efficiency and estimation accuracy.


---

## Body

## 1. Introduction

Direction of arrival (DOA) estimation has been a key issue in many practical applications such as radar, wireless communication system, and seismology [1, 2]. The vector sensor array, which offers advantages such as good robustness towards channel fading and strong immunity to interference, has been introduced for DOA estimation [3–6]. Typically, the subspace-based methods such as multiple signal classification (MUSIC) [7] and estimation of signal parameters via rotation invariance techniques (ESPRIT) [8] can be extended for the vector sensor array. More specifically, the polarized MUSIC-based methods [9–12] and the polarized ESPRIT-based methods [13–16] were demonstrated to have enhanced estimation performance as compared to the traditional MUSIC and ESPRIT methods with scalar sensor arrays. However, all the aforementioned methods operate under the assumption that the impinging sources are uncorrelated, while this assumption is often not true in practical scenarios due to multipath propagation. In such scenarios, the sources from the identical target may undergo reflection from various surfaces, and then the received sources may be a mixture of uncorrelated and coherent sources. Therefore, the performance of these methods would critically degrade because the existence of coherent sources directly causes the rank deficiency of the array covariance matrix.To solve the aforementioned problem, several “decorrelation” methods have been reported in [17–21]. A polarization smoothing (PS) technique was first developed in [17] to handle the coherent sources by using a vector sensor array. Subsequently, a modified polarization difference smoothing (PDS) method [18] was proposed in conjunction with the propagator method. Theoretically, the maximum number of resolvable coherent sources of the PDS method was limited to six. Gu et al. [19] introduced a propagator-based angle and polarization estimation method with an extra isolated vector sensor. In practice, a major limitation of these methods is their focus on addressing the coherent sources, while the coexistence of both uncorrelated and coherent sources is a common scenario for many practical applications owing to multipath propagation [22]. Another method for coherent sources, called polarization angular smoothing algorithm (PAS) [20], utilizes the cross-correlations among six subarrays and can be extended for scenarios of coexistent uncorrelated and coherent sources. Unfortunately, the simultaneous estimation of the uncorrelated and coherent sources using this method results in mutual interference between uncorrelated and coherent sources and poor utilization of the array aperture. Following the technique of [20], an improved polarization angular smoothing algorithm (IPAS) [21] was developed with an extended array aperture, which takes special consideration of the coexistence of uncorrelated and coherent sources. However, a loss of power may occur at the coherent sources due to the utilization of spatial differencing technique. All of these aforementioned “decorrelation” methods operate with spatially collocated six-component vector sensor arrays that are easily subjected to mutual coupling across the collocated antennas, and the utilization of the six-component vector sensor array results in an increase in hardware costs for antenna arrays. Moreover, these methods are unable to estimate the polarization parameters that are useful for angular resolution, target classification, and recognition [23].To address these issues, we present a novel method in this paper for jointly estimating the angle and the polarization under the coexistence of the uncorrelated and coherent sources in this paper using a dual-polarization uniform linear array (ULA). On the basis of the modulus property of eigenvalues and rotational invariance, the uncorrelated sources are firstly distinguished from the coherent sources, and their corresponding angles are estimated. Subsequently, the uncorrelated array response matrix corresponding to each uncorrelated source is obtained from the estimated source subspace and the associated eigenvector matrix. The associated polarization parameters are obtained by exploiting the inherent relationship between the odd and even rows of the uncorrelated array response matrix using elementwise division operation. For the remaining coherent sources, the array response matrix of each coherent group is estimated in a way similar to that followed for the uncorrelated array response matrix, with which two Hankel matrices are constructed for “decorrelation.” The angles of each coherent group are estimated via construction of two pairs of rotational-invariant submatrices. Finally, the least-square solution to the coherent polarization equation is derived, and the associated coherent polarization parameters are obtained accordingly. To be more specific, the main contributions of this paper are as follows:(1)
The proposed method considers the joint angle and polarization estimation for a mixture of uncorrelated and coherent sources, unlike most of the existing “decorrelation” methods that focus only on the angle estimation of coherent sources.
(2)
By utilizing a dual-polarization vector sensor array, the problem of mutual coupling across the collocated antennas is alleviated. In addition, the costs of antenna hardware are also reduced.
(3)
By employing the modulus property of eigenvalues, the uncorrelated sources are distinguished from the coherent sources without a loss of power at coherent sources. Based on estimated array response matrix of each uncorrelated source and that of each coherent group, the corresponding angle and polarization parameters are estimated separately, which avoids the need of three-dimensional (3D) spectral search.
(4)
The identifiability and computational complexity of the proposed method are discussed.The mathematical notations used throughout this paper are as follows. Vectors and matrices are, respectively, denoted by lowercase and uppercase bold-faced italicized letters.(
·
)
T, (
·
)
∗, (
·
)
H, (
·
)
-
1, (
·
)
†, ⊗, and E
· represent transpose, conjugate, conjugate transpose, inverse, Moore-Penrose inverse, Kronecker product, and the statistical expectation, respectively. 0
m
×
n represents m
×
n null matrix, I
m
m
×
m identity matrix, ·
F the Frobenius norm, and .
/ the elementwise division. Besides, ∂
f
F
/
∂
F denotes the derivative of f
F with respect to the matrix F; d
i
a
g
· and b
l
k
d
i
a
g
· denote a diagonal matrix and a block diagonal matrix, respectively. F
a
:
b
,
c
:
d denotes a submatrix constructed by the elements from rows a to b and columns c to d of F.The rest of the paper is organized as follows. The angle and polarization estimation model in the presence of multipath propagation is formulated in Section2. Section 3 presents the details of the proposed angle and polarization estimation method under the coexistence of uncorrelated and coherent sources. The identifiability and computational complexity of the proposed method are discussed in Section 4. Section 5 discusses the simulation performance of the proposed method. Conclusions are drawn in Section 6.


## 2. Problem Formulation

Consider a ULA consisting ofM dual-polarization sensors (i.e., crossed dipoles) placed along the y-axis with interelement spacing d, as depicted in Figure 1. θ
∈
0
,
π and φ
∈
0,2
π signify the elevation angle and the azimuth angle measured from the positive z- and x-axes, respectively. For simplicity, it is assumed that the impinging source is in the y-z plane; that is, φ
=
0. Assume that a total of K completely polarized narrowband transverse electromagnetic (TEM) waves impinge on the ULA, and the electric field is described in Cartesian coordinate as(1)
E
=
-
E
φ
e
x
+
E
θ
cos
⁡
θ
e
y
-
E
θ
sin
⁡
θ
e
z
,where e
x, e
y, and e
z are the unit vectors along the x-, y-, and z-axes; E
φ
=
E
o
cos
⁡
γ and E
θ
=
E
o
sin
⁡
γ
e
j
η are, respectively, the horizontal and the vertical components of a polarization ellipse. E
o represents the source amplitude (an arbitrary nonzero complex constant) and γ
∈
0
,
π
/
2 refers to the auxiliary polarization angle and η
∈
-
π
,
π refers to the polarization phase difference. The dual-polarization ULA configured in Figure 1 is known to only receive the electric field components of the waves along the x- and y-axes. Therefore, the source vectors collected by the mth vector sensor for polarization x and polarization y are, respectively, expressed as(2)
x
m
x
t
=
-
∑
k
=
1
K
s
k
t
cos
⁡
γ
k
e
-
j
2
π
m
-
1
d
s
i
n
θ
k
/
λ
+
n
m
x
t
,
(3)
x
m
y
t
=
-
∑
k
=
1
K
s
k
t
cos
⁡
θ
k
sin
⁡
γ
k
e
j
η
k
e
-
j
2
π
m
-
1
d
s
i
n
θ
k
/
λ
+
n
m
y
t
,where m
∈
1
,
M, n
m
[
x
]
(
t
), and n
m
[
y
]
(
t
) denote the noise components of polarization x and polarization y, respectively, and λ is the carrier wavelength. Combining (2) and (3), we have(4)
x
m
t
=
x
m
x
t
T
,
x
m
y
t
T
Twith n
m
(
t
)
=
n
m
x
t
T
,
n
m
y
t
T
T being the received noise vector. In realistic cases, the coherent sources are often susceptible to multipath propagation. The K impinging sources, parameterized by θ
1
,
γ
1
,
η
1
,
θ
2
,
γ
2
,
η
2
,
…
,
θ
K
,
γ
K
,
η
K, are composed of D groups (each group having p
k coherent sources) of K
c coherent and K
u uncorrelated sources, where K
c
=
K
-
K
u
=
∑
k
=
1
D
p
k. The entire 2
M
×
1 array output vector of the ULA at time t is written as(5)
X
t
=
∑
k
=
1
K
u
a
θ
k
s
k
t
+
∑
k
=
K
u
+
1
K
u
+
D
∑
p
=
1
P
D
a
θ
k
,
p
ς
k
,
p
s
k
t
+
N
twhich can further be rewritten in a matrix form as (6)
X
t
=
A
u
θ
,
γ
,
η
S
u
t
+
A
c
θ
,
γ
,
η
Γ
S
c
t
+
N
t
=
A
θ
,
γ
,
η
E
S
t
+
N
t
,where X
(
t
)
=
x
1
t
,
x
2
t
,
…
,
x
M
(
t
)
T, S
(
t
)
=
s
1
t
,
s
2
t
,
…
,
s
K
(
t
)
T, and N
(
t
)
=
n
1
t
,
n
2
t
,
…
,
n
M
(
t
)
T. For brevity, the (
K
u
+
D
)
×
1 source vector can be described as S
(
t
)
=
S
u
T
(
t
)
,
S
c
T
(
t
)
T with S
u
(
t
)
=
s
1
t
,
s
2
t
,
…
,
s
K
u
(
t
)
T and S
c
(
t
)
=
s
K
u
+
1
t
,
s
K
u
+
2
t
,
…
,
s
K
u
+
D
(
t
)
T being the source vectors associated with the uncorrelated and coherent sources, respectively. E is a K
×
(
K
u
+
D
) block diagonal matrix defined as E
=
b
l
k
d
i
a
g
I
K
u
,
Γ, where Γ is the fading coefficient matrix whose kth column is ς
k
=
ς
k
,
1
,
ς
k
,
2
,
…
,
ς
k
,
p
k
T for k
=
K
u
+
1
,
…
,
K
u
+
D. The 2
M
×
K array response matrix A
(
θ
,
γ
,
η
) is defined as A
(
θ
,
γ
,
η
)
=
A
u
(
θ
,
γ
,
η
)
,
A
c
(
θ
,
γ
,
η
), where A
u
(
θ
,
γ
,
η
)
=
a
θ
1
,
γ
1
,
η
1
,
a
θ
2
,
γ
2
,
η
2
,
…
,
a
(
θ
K
u
,
γ
K
u
,
η
K
u
) corresponds to the K
u uncorrelated sources and A
c
(
θ
,
γ
,
η
)
=
A
c
,
K
u
+
1
θ
,
γ
,
η
,
A
c
,
K
u
+
2
θ
,
γ
,
η
,
…
,
A
c
,
K
u
+
D
(
θ
,
γ
,
η
) corresponds to the K
c coherent sources with A
c
,
k
(
θ
,
γ
,
η
)
=
a
θ
k
,
1
,
γ
k
,
1
,
η
k
,
1
,
a
θ
k
,
2
,
γ
k
,
2
,
η
k
,
2
,
…
,
a
(
θ
k
,
p
k
,
γ
k
,
p
k
,
η
k
,
p
k
) being the array response matrix with respect to the kth group of coherent sources. The kth column vector of the array response matrix A
(
θ
,
γ
,
η
) is defined as(7)
a
θ
k
,
γ
k
,
η
k
=
q
θ
k
⊗
c
θ
k
,
γ
k
,
η
k
,where the source steering vector q
(
θ
k
) and polarization steering vector c
(
θ
k
,
φ
k
,
γ
k
) are, respectively, defined as (8)
q
θ
k
=
1
,
e
-
j
2
π
d
s
i
n
θ
k
/
λ
,
…
,
e
-
j
2
π
M
-
1
d
s
i
n
θ
k
/
λ
T
,
(9)
c
θ
k
,
γ
k
,
η
k
=
-
cos
⁡
γ
k
,
cos
⁡
θ
k
sin
⁡
γ
k
e
j
η
k
T
.Figure 1
Uniform linear array of dual-polarization vector sensor.The objective of the proposed method is to determine the angle and polarization parametersθ
k
,
γ
k
,
η
k
,
k
=
1,2
,
…
,
K under the condition of coexisting uncorrelated and coherent sources. For notational convenience, A
(
θ
,
γ
,
η
), A
u
(
θ
,
γ
,
η
), A
c
(
θ
,
γ
,
η
), and c
(
θ
k
,
γ
k
,
η
k
) are, respectively, substituted by A, A
u, A
c, and c
k in the following analysis.The basic assumptions followed throughout this paper are as follows:(A1)
S
(
t
) and N
(
t
) are the zero-mean uncorrelated stationary Gaussian random processes that are uncorrelated with each other. Coherent sources s
k
(
t
)
k
=
K
u
+
1
K
u
+
D in different coherent groups are mutually uncorrelated, and they are also uncorrelated with the uncorrelated sources s
k
(
t
)
k
=
1
K
u.
(A2)
The number of uncorrelated and coherent sources, coherent groups, and fading coefficients (i.e., the values ofK
u, K
c, D, and ς
k
,
p) can be estimated by using the source number estimation [24] and the fading coefficients estimation [25].
(A3)
To obviate the problem of phase ambiguity, the interelement spacing of the dual-polarization ULA satisfiesd
≤
λ
/
2, and the number of sources is less than the number of sensors; that is, K
u
+
D
<
M.


## 3. Parameter Estimation

In this section, the angle and polarization estimation method is derived for a mixture of uncorrelated and coherent sources by using a dual-polarization ULA. Based on the modulus property of eigenvalues, the uncorrelated sources are distinguished from the coherent sources. This reduces the mutual interference between uncorrelated and coherent sources and enlarges the effective array aperture. The angle and polarization parameters of each uncorrelated source and that of each coherent group are estimated separately by estimating the corresponding array response matrix, thus eliminating the need of computationally intensive 3D spectral search.


### 3.1. Parameter Estimation for Uncorrelated Sources

The covariance matrix ofX
(
t
) with the size 2
M
×
2
M is expressed as(10)
R
=
E
X
t
X
H
t
=
A
E
R
s
E
H
A
H
+
σ
n
2
I
=
A
u
R
u
A
u
H
+
A
c
Γ
R
c
Γ
H
A
c
H
+
σ
n
2
I
,where the source covariance matrix R
s
=
E
S
(
t
)
S
H
(
t
) is segmented into two parts R
s
=
R
u
,
R
c, where R
u
=
E
S
u
(
t
)
S
u
H
(
t
) and R
c
=
E
S
c
(
t
)
S
c
H
(
t
) are the uncorrelated and coherent source covariance matrices and σ
n
2 denotes the noise variance. In the case of K sources comprising K
u uncorrelated and D groups of K
c coherent sources, R
s is of rank K
u
+
D. By applying eigenvalue decomposition (EVD) to R, the source subspace E
s is obtained from the eigenvectors corresponding to the K
u
+
D largest eigenvalues.It is noted that the columns ofE
s and A
E span the same subspace, such that(11)
E
s
=
A
E
T
=
A
u
,
A
c
Γ
T
=
C
u
C
c
Γ
C
u
Δ
u
C
c
Δ
c
Γ
⋮
⋮
C
u
Δ
u
M
-
1
C
c
Δ
c
M
-
1
Γ
T
,where T is a unique (
K
u
+
D
)
×
(
K
u
+
D
) full rank matrix and Δ
u
=
d
i
a
g
e
-
j
2
π
d
s
i
n
θ
1
/
λ
,
e
-
j
2
π
d
s
i
n
θ
2
/
λ
,
…
,
e
-
j
2
π
d
s
i
n
θ
K
u
/
λ
∈
C
K
u
×
K
u and Δ
c
=
d
i
a
g
{
e
-
j
2
π
d
s
i
n
θ
K
u
+
1,1
/
λ
,
…
,
e
-
j
2
π
d
s
i
n
θ
K
u
+
1
,
p
1
/
λ
,
…
,
e
-
j
2
π
d
s
i
n
θ
K
u
+
D
,
1
/
λ
,
…
,
e
-
j
2
π
d
s
i
n
θ
K
u
+
D
,
p
D
/
λ
}
∈
C
K
c
×
K
c are the two diagonal matrices that depend only on the arrival-angles. C
u and C
c are, respectively, called the uncorrelated and coherent polarization factor matrices defined by(12)
C
u
=
c
1
,
c
2
,
…
,
c
K
u
=
-
cos
⁡
γ
1
-
cos
⁡
γ
2
⋯
-
cos
⁡
γ
K
u
cos
⁡
θ
1
sin
⁡
γ
1
e
j
η
1
cos
⁡
θ
2
sin
⁡
γ
2
e
j
η
2
⋯
cos
⁡
θ
K
u
sin
⁡
γ
K
u
e
j
η
K
u
,
(13)
C
c
=
c
K
u
+
1,1
,
…
,
c
K
u
+
1
,
p
1
,
…
,
c
K
u
+
D
,
p
D
=
-
cos
⁡
γ
K
u
+
1,1
⋯
-
cos
⁡
γ
K
u
+
1
,
p
1
⋯
-
cos
⁡
γ
K
u
+
D
,
p
D
cos
⁡
θ
K
u
+
1,1
sin
⁡
γ
K
u
+
1,1
e
j
η
K
u
+
1,1
⋯
cos
⁡
θ
K
u
+
1
,
p
1
sin
⁡
γ
K
u
+
1
,
p
1
e
j
η
K
u
+
1
,
p
1
⋯
cos
⁡
θ
K
u
+
D
,
p
D
sin
⁡
γ
K
u
+
D
,
p
D
e
j
η
K
u
+
D
,
p
D
.According to the inherent rotational invariance,E
s can be divided into two 2
(
M
-
1
)
×
(
K
u
+
D
) overlapped submatrices, where the lth submatrix can be expressed as(14)
E
s
,
l
=
J
l
E
swith the selection matrix J
l defined as J
l
=
0
2
(
M
-
1
)
×
2
(
l
-
1
)
I
2
(
M
-
1
)
0
2
(
M
-
1
)
×
(
4
-
2
l
) for l
=
1,2. According to (11) and (14), we have (15)
E
s
,
1
†
E
s
,
2
=
T
-
1
Δ
T
,where the block diagonal matrix Δ, comprising both uncorrelated and coherent angle information, is expressed as Δ
=
b
l
k
d
i
a
g
Δ
u
,
Γ
†
Δ
c
Γ. As can be seen in (15), the diagonal matrix Δ is composed of K
u
+
D eigenvalues of the matrix E
s
,
1
†
E
s
,
2, and the full rank matrix T
-
1 is composed of the corresponding eigenvectors of matrix E
s
,
1
†
E
s
,
2. Based on the modulus property outlined in [26], the moduli of the elements in Δ, corresponding to uncorrelated sources, are approximately equivalent to 1 in the case of noise disturbance, while those corresponding to coherent groups are significantly away from 1. As a result, the uncorrelated sources are distinguished from coherent sources, and the angles of uncorrelated sources are thereby resolved.K
u columns of T
-
1 corresponding to K
u uncorrelated sources are extracted in order to construct the matrix T
u
-
1. Similarly, the remaining D columns, corresponding to D coherent groups, are chosen from T
-
1 to construct matrix T
c
-
1. According to (11), the estimation of A
u is defined as (16)
A
^
u
=
E
s
T
u
-
1
=
C
u
C
u
Δ
u
⋮
C
u
Δ
u
M
-
1
=
-
cos
⁡
γ
1
⋯
-
cos
⁡
γ
K
u
cos
⁡
θ
1
sin
⁡
γ
1
e
j
η
1
⋯
cos
⁡
θ
K
u
sin
⁡
γ
K
u
e
j
η
K
u
-
cos
⁡
γ
1
e
-
j
2
π
d
s
i
n
θ
1
/
λ
⋯
-
cos
⁡
γ
K
u
e
-
j
2
π
d
s
i
n
θ
K
u
/
λ
cos
⁡
θ
1
sin
⁡
γ
1
e
-
j
2
π
d
s
i
n
θ
1
/
λ
⋯
cos
⁡
θ
K
u
sin
⁡
γ
K
u
e
j
η
K
u
e
-
j
2
π
d
s
i
n
θ
K
u
/
λ
⋮
⋱
⋮
-
cos
⁡
γ
1
e
-
j
2
π
M
-
1
d
s
i
n
θ
1
/
λ
⋯
-
cos
⁡
γ
K
u
e
-
j
2
π
M
-
1
d
s
i
n
θ
K
u
/
λ
cos
⁡
θ
1
sin
⁡
γ
1
e
-
j
2
π
M
-
1
d
s
i
n
θ
1
/
λ
⋯
cos
⁡
θ
K
u
sin
⁡
γ
K
u
e
j
η
K
u
e
-
j
2
π
M
-
1
d
s
i
n
θ
K
u
/
λ
.For thekth k
=
1,2
,
…
,
K
u uncorrelated source, the relevant array response matrix A
^
u
,
k is formulated on similar lines as for (16); that is, A
^
u
,
k
=
E
s
T
u
,
k
-
1, where T
u
,
k
-
1 is the eigenvector of the kth uncorrelated source extracted from T
u
-
1. Further, the corresponding auxiliary polarization angle γ
^
k and the polarization phase difference η
^
k of the kth uncorrelated source are, respectively, obtained as(17)
γ
^
k
=
1
M
∑
i
=
1
M
t
a
n
-
1
A
^
u
,
k
2
i
,
k
.
/
A
^
u
,
k
2
i
-
1
,
k
cos
⁡
θ
k
,
(18)
η
^
k
=
1
M
∑
i
=
1
M
arg
⁡
A
^
u
,
k
2
i
,
k
.
/
A
^
u
,
k
2
i
-
1
,
k
.It can be observed from (17) and (18) that the polarization parameters of the uncorrelated sources are estimated by taking advantages of the inherent structure of A
^
u
,
k, which is easy to implement by using elementwise division operation. In addition, the proposed method accomplishes the estimation of angle and polarization parameters for the uncorrelated sources effectively without resorting to parameter matching.


### 3.2. Parameter Estimation for Coherent Sources

Similar to the estimation ofA
u outlined in Section 3.1, the array response matrix of the kth (k
=
K
u
+
1
,
K
u
+
2
,
…
,
K
u
+
D) coherent group A
c
,
k can be estimated as (19)
A
^
c
,
k
=
E
s
T
c
,
k
-
1
=
C
c
,
k
ς
k
C
c
,
k
Δ
c
,
k
ς
k
⋮
C
c
,
k
Δ
c
,
k
M
-
1
ς
k
.This can further be rewritten in an extensive form as(20)
A
^
c
,
k
=
-
ς
k
,
1
cos
⁡
γ
k
,
1
-
⋯
-
ς
k
,
p
k
cos
⁡
γ
k
,
p
k
ς
k
,
1
cos
⁡
θ
k
,
1
sin
⁡
γ
k
,
1
e
j
η
k
,
1
+
⋯
+
ς
k
,
p
k
cos
⁡
θ
k
,
p
k
sin
⁡
γ
k
,
p
k
e
j
η
k
,
p
k
-
ς
k
,
1
cos
⁡
γ
k
,
1
e
-
j
2
π
d
s
i
n
θ
k
,
1
/
λ
-
⋯
-
ς
k
,
p
k
cos
⁡
γ
k
,
p
k
e
-
j
2
π
d
s
i
n
θ
k
,
p
k
/
λ
ς
k
,
1
cos
⁡
θ
k
,
1
sin
⁡
γ
k
,
1
e
-
j
2
π
d
s
i
n
θ
k
,
1
/
λ
+
⋯
+
ς
k
,
p
k
cos
⁡
θ
k
,
p
k
sin
⁡
γ
k
,
p
k
e
j
η
k
,
p
k
e
-
j
2
π
d
s
i
n
θ
k
,
p
k
/
λ
⋮
-
ς
k
,
1
cos
⁡
γ
k
,
1
e
-
j
2
π
M
-
1
d
s
i
n
θ
k
,
1
/
λ
-
⋯
-
ς
k
,
p
k
cos
⁡
γ
k
,
p
k
e
-
j
2
π
M
-
1
d
s
i
n
θ
k
,
p
k
/
λ
ς
k
,
1
cos
⁡
θ
k
,
1
sin
⁡
γ
k
,
1
e
-
j
2
π
M
-
1
d
s
i
n
θ
k
,
1
/
λ
+
⋯
+
ς
k
,
p
k
cos
⁡
θ
k
,
p
k
sin
⁡
γ
k
,
p
k
e
j
η
k
,
p
k
e
-
j
2
π
M
-
1
d
s
i
n
θ
k
,
p
k
/
λ
,where C
c
,
k
=
c
k
,
1
,
c
k
,
2
,
…
,
c
k
,
p
k and Δ
c
,
k
=
d
i
a
g
e
-
j
2
π
d
s
i
n
θ
k
,
1
/
λ
,
…
,
e
-
j
2
π
d
s
i
n
θ
k
,
p
k
/
λ. Note that the odd and even rows of A
^
c
,
k characterize the array response submatrix of x- and y-axes components of the dual-polarization vector sensor array, respectively. Thus, we divide A
^
c
,
k of size 2
M
×
1 into two M
×
1 submatrices using the following equation:(21)
A
^
c
,
k
i
=
G
i
T
A
^
c
,
k
,
i
=
1,2such that G
1 and G
2 are two exchange matrices, defined as (22)
G
1
=
g
1
,
g
3
,
…
,
g
2
M
-
1
,
G
2
=
g
2
,
g
4
,
…
,
g
2
M
,where g
i is a 2
M
×
1 vector having the element on the ith row as one and the remaining elements as zeros. For the purpose of “decorrelation,” the two Hankel matrices constructed by the array response matrices of x- and y-axes components with respect to the kth coherent group are given as(23)
B
k
1
=
A
^
c
,
k
1
1
A
^
c
,
k
1
2
⋯
A
^
c
,
k
1
p
k
+
1
A
^
c
,
k
1
2
A
^
c
,
k
1
3
⋯
A
^
c
,
k
1
p
k
+
2
⋮
⋮
⋱
⋮
A
^
c
,
k
1
M
-
p
k
A
^
c
,
k
1
M
-
p
k
+
1
⋯
A
^
c
,
k
1
M
,
(24)
B
k
2
=
A
^
c
,
k
2
1
A
^
c
,
k
2
2
⋯
A
^
c
,
k
2
p
k
+
1
A
^
c
,
k
2
2
A
^
c
,
k
2
3
⋯
A
^
c
,
k
2
p
k
+
2
⋮
⋮
⋱
⋮
A
^
c
,
k
2
M
-
p
k
A
^
c
,
k
2
M
-
p
k
+
1
⋯
A
^
c
,
k
2
M
,where M
-
p
k
>
p
k. It is easily proven that the two matrices B
k
(
1
) and B
k
(
2
) have a full rank and can be further expressed as(25)
B
k
1
=
C
c
k
,
1
ς
k
C
c
k
,
1
Δ
c
,
k
ς
k
⋯
C
c
k
,
1
Δ
c
,
k
p
k
ς
k
C
c
k
,
1
Δ
c
,
k
ς
k
C
c
k
,
1
Δ
c
,
k
2
ς
k
⋯
C
c
k
,
1
Δ
c
,
k
p
k
+
1
ς
k
⋮
⋮
⋱
⋮
C
c
k
,
1
Δ
c
,
k
M
-
p
k
-
1
ς
k
C
c
k
,
1
Δ
c
,
k
M
-
p
k
ς
k
⋯
C
c
k
,
1
Δ
c
,
k
M
-
1
ς
k
,
(26)
B
k
2
=
C
c
k
,
2
ς
k
C
c
k
,
2
Δ
c
,
k
ς
k
⋯
C
c
k
,
2
Δ
c
,
k
p
k
ς
k
C
c
k
,
2
Δ
c
,
k
ς
k
C
c
k
,
2
Δ
c
,
k
2
ς
k
⋯
C
c
k
,
2
Δ
c
,
k
p
k
+
1
ς
k
⋮
⋮
⋱
⋮
C
c
k
,
2
Δ
c
,
k
M
-
p
k
-
1
ς
k
C
c
k
,
2
Δ
c
,
k
M
-
p
k
ς
k
⋯
C
c
k
,
2
Δ
c
,
k
M
-
1
ς
k
,where C
c
k
,
1 and C
c
k
,
2 are, respectively, composed of the first and the second rows of C
c
,
k. The matrix Δ
c
,
k
=
d
i
a
g
e
-
j
2
π
d
s
i
n
θ
k
,
1
/
λ
,
…
,
e
-
j
2
π
d
s
i
n
θ
k
,
p
k
/
λ corresponding to the kth (
k
=
K
u
+
1
,
…
,
K
u
+
D
) coherent group can be extracted from Δ
c. In view of the fact that B
k
(
1
) and B
k
(
2
) have the same rotational-invariant structures, either of them can be utilized for the estimation of coherent angles. In this study, B
k
(
1
) is taken as an example. First, two rotational-invariant submatrix pairs are constructed: the first pair is B
k
,
r
1
(
1
)
=
B
k
(
1
)
1
:
M
-
p
k
-
1
,
: and B
k
,
r
2
(
1
)
=
B
k
(
1
)
2
:
M
-
p
k
,
:; the second pair is B
k
,
l
1
(
1
)
=
B
k
(
1
)
:
,
1
:
M
-
p
k
-
1 and B
k
,
l
2
(
1
)
=
B
k
(
1
)
:
,
2
:
M
-
p
k. Subsequently, the rotational invariance can be applied to the two submatrix pairs twice, which results in two groups of coherent angle estimation results θ
^
k
,
1
1
,
θ
^
k
,
2
1
,
…
,
θ
^
k
,
p
k
1 and θ
^
k
,
1
2
,
θ
^
k
,
2
2
,
…
,
θ
^
k
,
p
k
2. The final coherent angle estimation is then achieved as θ
^
k
,
1
,
θ
^
k
,
2
,
…
,
θ
^
k
,
p
k
=
θ
^
k
,
1
1
+
θ
^
k
,
1
2
/
2
,
θ
^
k
,
2
1
+
θ
^
k
,
2
2
/
2
,
…
,
θ
^
k
,
p
k
1
+
θ
^
k
,
p
k
2
/
2 that allows more accurate angle estimation than the conventional ESPRIT method along with a slight computational gain.For further coherent polarization estimation,B
k
(
1
) and B
k
(
2
) can be rewritten as(27)
B
k
1
=
C
c
k
,
1
C
c
k
,
1
Δ
c
,
k
⋮
C
c
k
,
1
Δ
c
,
k
M
-
p
k
-
1
ς
k
Δ
c
,
k
ς
k
⋯
Δ
c
,
k
p
k
ς
k
,
(28)
B
k
2
=
C
c
k
,
2
C
c
k
,
2
Δ
c
,
k
⋮
C
c
k
,
2
Δ
c
,
k
M
-
p
k
-
1
ς
k
Δ
c
,
k
ς
k
⋯
Δ
c
,
k
p
k
ς
k
.In order to determine the polarization parameters of the coherent sources, the theory of least-squares is adopted such that(29)
Δ
Q
k
=
min
⁡
B
k
1
Q
k
-
B
k
2
F
2
,where (29) is referred to as the coherent polarization equation. The derivative of Δ
Q
k with respect to the coherent polarization matrix Q
k is defined as (30)
∂
Δ
Q
k
∂
Q
k
=
-
B
k
2
T
B
k
1
-
B
k
1
T
B
k
2
+
B
k
1
T
B
k
1
Q
k
+
Q
k
T
B
k
1
T
B
k
1
.The solution to (29) is acquired by setting the equality in (30) to be zero. Thus, we have(31)
Q
k
=
B
k
1
T
B
k
1
-
1
B
k
1
T
B
k
2
=
B
k
1
†
B
k
2
.By substituting (27) and (28) into (31), Q
k can be further reformulated as (see Appendix for details)(32)
Q
k
=
C
c
k
,
1
C
c
k
,
1
Δ
c
,
k
⋮
C
c
k
,
1
Δ
c
,
k
M
-
p
k
-
1
ς
k
Δ
c
,
k
ς
k
⋯
Δ
c
,
k
p
k
ς
k
†
C
c
k
,
2
C
c
k
,
2
Δ
c
,
k
⋮
C
c
k
,
2
Δ
c
,
k
M
-
p
k
-
1
ς
k
Δ
c
,
k
ς
k
⋯
Δ
c
,
k
p
k
ς
k
=
ς
k
Δ
c
,
k
ς
k
⋯
Δ
c
,
k
p
k
ς
k
†
μ
k
,
1
μ
k
,
2
⋱
μ
k
,
p
k
ς
k
Δ
c
,
k
ς
k
⋯
Δ
c
,
k
p
k
ς
k
,where μ
k
,
i
=
-
tan
⁡
γ
k
,
i
cos
⁡
θ
k
,
i
e
j
η
k
,
i
,
i
=
1,2
,
…
,
p
k. Equation (32) indicates that the polarization information related to the kth group coherent source can be obtained from the eigenvalues of Q
k. Thus, the estimations of polarization phase difference are given by (33)
η
^
k
,
i
=
-
arg
⁡
μ
k
,
i
,
k
=
K
u
+
1
,
K
u
+
2
,
…
,
K
u
+
D
,
i
=
1,2
,
…
,
p
k
.To achieve the estimation of coherent auxiliary polarization angles, the associated angle and polarization phase differences must obey a one-to-one relationship. For this purpose, we resort to a simple pair-matching method outlined in [14]. The matching method is implemented via a simple eigenvalue-matching operation, which is effective at the cost of a negligible increase in computational cost. The estimated auxiliary polarization angles are obtained as (34)
γ
^
k
,
i
=
t
a
n
-
1
μ
k
,
i
cos
⁡
θ
k
,
i
,
k
=
K
u
+
1
,
K
u
+
2
,
…
,
K
u
+
D
,
i
=
1,2
,
…
,
p
k
.The estimation of joint angle and polarization is therefore accomplished using the proposed method under the coexistence of both uncorrelated and coherent sources. The major steps are summarized as follows.(1)
Calculate the array covariance matrixR in (10) via the sample estimation R
^
=
∑
n
=
1
N
X
(
t
n
)
X
H
(
t
n
)
/
N, where N is the snapshot number.
(2)
Based on the moduli property of the eigenvalues, the uncorrelated sources are firstly separated from the coherent sources, and the uncorrelated angle parameters are then estimated by exploiting the rotational-invariance properties according to (11), (14), and (15). Subsequently, the associated auxiliary polarization angle and the polarization phase difference are estimated by (17) and (18).
(3)
The coherent array response matrix is estimated according to (19)–(22) and is then divided into two submatrices A
^
c
,
k
(
1
) and A
^
c
,
k
(
2
). Further, two Hankel matrices B
k
(
1
) and B
k
(
2
) are constructed for “decorrelating” via (23)–(26), and the estimation of coherent angles is obtained by utilizing two rotational-invariant submatrix pairs. On the basis of the least-square theory, the estimations of coherent auxiliary polarization angle and the polarization phase difference are obtained from (29)–(34).


## 3.1. Parameter Estimation for Uncorrelated Sources

The covariance matrix ofX
(
t
) with the size 2
M
×
2
M is expressed as(10)
R
=
E
X
t
X
H
t
=
A
E
R
s
E
H
A
H
+
σ
n
2
I
=
A
u
R
u
A
u
H
+
A
c
Γ
R
c
Γ
H
A
c
H
+
σ
n
2
I
,where the source covariance matrix R
s
=
E
S
(
t
)
S
H
(
t
) is segmented into two parts R
s
=
R
u
,
R
c, where R
u
=
E
S
u
(
t
)
S
u
H
(
t
) and R
c
=
E
S
c
(
t
)
S
c
H
(
t
) are the uncorrelated and coherent source covariance matrices and σ
n
2 denotes the noise variance. In the case of K sources comprising K
u uncorrelated and D groups of K
c coherent sources, R
s is of rank K
u
+
D. By applying eigenvalue decomposition (EVD) to R, the source subspace E
s is obtained from the eigenvectors corresponding to the K
u
+
D largest eigenvalues.It is noted that the columns ofE
s and A
E span the same subspace, such that(11)
E
s
=
A
E
T
=
A
u
,
A
c
Γ
T
=
C
u
C
c
Γ
C
u
Δ
u
C
c
Δ
c
Γ
⋮
⋮
C
u
Δ
u
M
-
1
C
c
Δ
c
M
-
1
Γ
T
,where T is a unique (
K
u
+
D
)
×
(
K
u
+
D
) full rank matrix and Δ
u
=
d
i
a
g
e
-
j
2
π
d
s
i
n
θ
1
/
λ
,
e
-
j
2
π
d
s
i
n
θ
2
/
λ
,
…
,
e
-
j
2
π
d
s
i
n
θ
K
u
/
λ
∈
C
K
u
×
K
u and Δ
c
=
d
i
a
g
{
e
-
j
2
π
d
s
i
n
θ
K
u
+
1,1
/
λ
,
…
,
e
-
j
2
π
d
s
i
n
θ
K
u
+
1
,
p
1
/
λ
,
…
,
e
-
j
2
π
d
s
i
n
θ
K
u
+
D
,
1
/
λ
,
…
,
e
-
j
2
π
d
s
i
n
θ
K
u
+
D
,
p
D
/
λ
}
∈
C
K
c
×
K
c are the two diagonal matrices that depend only on the arrival-angles. C
u and C
c are, respectively, called the uncorrelated and coherent polarization factor matrices defined by(12)
C
u
=
c
1
,
c
2
,
…
,
c
K
u
=
-
cos
⁡
γ
1
-
cos
⁡
γ
2
⋯
-
cos
⁡
γ
K
u
cos
⁡
θ
1
sin
⁡
γ
1
e
j
η
1
cos
⁡
θ
2
sin
⁡
γ
2
e
j
η
2
⋯
cos
⁡
θ
K
u
sin
⁡
γ
K
u
e
j
η
K
u
,
(13)
C
c
=
c
K
u
+
1,1
,
…
,
c
K
u
+
1
,
p
1
,
…
,
c
K
u
+
D
,
p
D
=
-
cos
⁡
γ
K
u
+
1,1
⋯
-
cos
⁡
γ
K
u
+
1
,
p
1
⋯
-
cos
⁡
γ
K
u
+
D
,
p
D
cos
⁡
θ
K
u
+
1,1
sin
⁡
γ
K
u
+
1,1
e
j
η
K
u
+
1,1
⋯
cos
⁡
θ
K
u
+
1
,
p
1
sin
⁡
γ
K
u
+
1
,
p
1
e
j
η
K
u
+
1
,
p
1
⋯
cos
⁡
θ
K
u
+
D
,
p
D
sin
⁡
γ
K
u
+
D
,
p
D
e
j
η
K
u
+
D
,
p
D
.According to the inherent rotational invariance,E
s can be divided into two 2
(
M
-
1
)
×
(
K
u
+
D
) overlapped submatrices, where the lth submatrix can be expressed as(14)
E
s
,
l
=
J
l
E
swith the selection matrix J
l defined as J
l
=
0
2
(
M
-
1
)
×
2
(
l
-
1
)
I
2
(
M
-
1
)
0
2
(
M
-
1
)
×
(
4
-
2
l
) for l
=
1,2. According to (11) and (14), we have (15)
E
s
,
1
†
E
s
,
2
=
T
-
1
Δ
T
,where the block diagonal matrix Δ, comprising both uncorrelated and coherent angle information, is expressed as Δ
=
b
l
k
d
i
a
g
Δ
u
,
Γ
†
Δ
c
Γ. As can be seen in (15), the diagonal matrix Δ is composed of K
u
+
D eigenvalues of the matrix E
s
,
1
†
E
s
,
2, and the full rank matrix T
-
1 is composed of the corresponding eigenvectors of matrix E
s
,
1
†
E
s
,
2. Based on the modulus property outlined in [26], the moduli of the elements in Δ, corresponding to uncorrelated sources, are approximately equivalent to 1 in the case of noise disturbance, while those corresponding to coherent groups are significantly away from 1. As a result, the uncorrelated sources are distinguished from coherent sources, and the angles of uncorrelated sources are thereby resolved.K
u columns of T
-
1 corresponding to K
u uncorrelated sources are extracted in order to construct the matrix T
u
-
1. Similarly, the remaining D columns, corresponding to D coherent groups, are chosen from T
-
1 to construct matrix T
c
-
1. According to (11), the estimation of A
u is defined as (16)
A
^
u
=
E
s
T
u
-
1
=
C
u
C
u
Δ
u
⋮
C
u
Δ
u
M
-
1
=
-
cos
⁡
γ
1
⋯
-
cos
⁡
γ
K
u
cos
⁡
θ
1
sin
⁡
γ
1
e
j
η
1
⋯
cos
⁡
θ
K
u
sin
⁡
γ
K
u
e
j
η
K
u
-
cos
⁡
γ
1
e
-
j
2
π
d
s
i
n
θ
1
/
λ
⋯
-
cos
⁡
γ
K
u
e
-
j
2
π
d
s
i
n
θ
K
u
/
λ
cos
⁡
θ
1
sin
⁡
γ
1
e
-
j
2
π
d
s
i
n
θ
1
/
λ
⋯
cos
⁡
θ
K
u
sin
⁡
γ
K
u
e
j
η
K
u
e
-
j
2
π
d
s
i
n
θ
K
u
/
λ
⋮
⋱
⋮
-
cos
⁡
γ
1
e
-
j
2
π
M
-
1
d
s
i
n
θ
1
/
λ
⋯
-
cos
⁡
γ
K
u
e
-
j
2
π
M
-
1
d
s
i
n
θ
K
u
/
λ
cos
⁡
θ
1
sin
⁡
γ
1
e
-
j
2
π
M
-
1
d
s
i
n
θ
1
/
λ
⋯
cos
⁡
θ
K
u
sin
⁡
γ
K
u
e
j
η
K
u
e
-
j
2
π
M
-
1
d
s
i
n
θ
K
u
/
λ
.For thekth k
=
1,2
,
…
,
K
u uncorrelated source, the relevant array response matrix A
^
u
,
k is formulated on similar lines as for (16); that is, A
^
u
,
k
=
E
s
T
u
,
k
-
1, where T
u
,
k
-
1 is the eigenvector of the kth uncorrelated source extracted from T
u
-
1. Further, the corresponding auxiliary polarization angle γ
^
k and the polarization phase difference η
^
k of the kth uncorrelated source are, respectively, obtained as(17)
γ
^
k
=
1
M
∑
i
=
1
M
t
a
n
-
1
A
^
u
,
k
2
i
,
k
.
/
A
^
u
,
k
2
i
-
1
,
k
cos
⁡
θ
k
,
(18)
η
^
k
=
1
M
∑
i
=
1
M
arg
⁡
A
^
u
,
k
2
i
,
k
.
/
A
^
u
,
k
2
i
-
1
,
k
.It can be observed from (17) and (18) that the polarization parameters of the uncorrelated sources are estimated by taking advantages of the inherent structure of A
^
u
,
k, which is easy to implement by using elementwise division operation. In addition, the proposed method accomplishes the estimation of angle and polarization parameters for the uncorrelated sources effectively without resorting to parameter matching.


## 3.2. Parameter Estimation for Coherent Sources

Similar to the estimation ofA
u outlined in Section 3.1, the array response matrix of the kth (k
=
K
u
+
1
,
K
u
+
2
,
…
,
K
u
+
D) coherent group A
c
,
k can be estimated as (19)
A
^
c
,
k
=
E
s
T
c
,
k
-
1
=
C
c
,
k
ς
k
C
c
,
k
Δ
c
,
k
ς
k
⋮
C
c
,
k
Δ
c
,
k
M
-
1
ς
k
.This can further be rewritten in an extensive form as(20)
A
^
c
,
k
=
-
ς
k
,
1
cos
⁡
γ
k
,
1
-
⋯
-
ς
k
,
p
k
cos
⁡
γ
k
,
p
k
ς
k
,
1
cos
⁡
θ
k
,
1
sin
⁡
γ
k
,
1
e
j
η
k
,
1
+
⋯
+
ς
k
,
p
k
cos
⁡
θ
k
,
p
k
sin
⁡
γ
k
,
p
k
e
j
η
k
,
p
k
-
ς
k
,
1
cos
⁡
γ
k
,
1
e
-
j
2
π
d
s
i
n
θ
k
,
1
/
λ
-
⋯
-
ς
k
,
p
k
cos
⁡
γ
k
,
p
k
e
-
j
2
π
d
s
i
n
θ
k
,
p
k
/
λ
ς
k
,
1
cos
⁡
θ
k
,
1
sin
⁡
γ
k
,
1
e
-
j
2
π
d
s
i
n
θ
k
,
1
/
λ
+
⋯
+
ς
k
,
p
k
cos
⁡
θ
k
,
p
k
sin
⁡
γ
k
,
p
k
e
j
η
k
,
p
k
e
-
j
2
π
d
s
i
n
θ
k
,
p
k
/
λ
⋮
-
ς
k
,
1
cos
⁡
γ
k
,
1
e
-
j
2
π
M
-
1
d
s
i
n
θ
k
,
1
/
λ
-
⋯
-
ς
k
,
p
k
cos
⁡
γ
k
,
p
k
e
-
j
2
π
M
-
1
d
s
i
n
θ
k
,
p
k
/
λ
ς
k
,
1
cos
⁡
θ
k
,
1
sin
⁡
γ
k
,
1
e
-
j
2
π
M
-
1
d
s
i
n
θ
k
,
1
/
λ
+
⋯
+
ς
k
,
p
k
cos
⁡
θ
k
,
p
k
sin
⁡
γ
k
,
p
k
e
j
η
k
,
p
k
e
-
j
2
π
M
-
1
d
s
i
n
θ
k
,
p
k
/
λ
,where C
c
,
k
=
c
k
,
1
,
c
k
,
2
,
…
,
c
k
,
p
k and Δ
c
,
k
=
d
i
a
g
e
-
j
2
π
d
s
i
n
θ
k
,
1
/
λ
,
…
,
e
-
j
2
π
d
s
i
n
θ
k
,
p
k
/
λ. Note that the odd and even rows of A
^
c
,
k characterize the array response submatrix of x- and y-axes components of the dual-polarization vector sensor array, respectively. Thus, we divide A
^
c
,
k of size 2
M
×
1 into two M
×
1 submatrices using the following equation:(21)
A
^
c
,
k
i
=
G
i
T
A
^
c
,
k
,
i
=
1,2such that G
1 and G
2 are two exchange matrices, defined as (22)
G
1
=
g
1
,
g
3
,
…
,
g
2
M
-
1
,
G
2
=
g
2
,
g
4
,
…
,
g
2
M
,where g
i is a 2
M
×
1 vector having the element on the ith row as one and the remaining elements as zeros. For the purpose of “decorrelation,” the two Hankel matrices constructed by the array response matrices of x- and y-axes components with respect to the kth coherent group are given as(23)
B
k
1
=
A
^
c
,
k
1
1
A
^
c
,
k
1
2
⋯
A
^
c
,
k
1
p
k
+
1
A
^
c
,
k
1
2
A
^
c
,
k
1
3
⋯
A
^
c
,
k
1
p
k
+
2
⋮
⋮
⋱
⋮
A
^
c
,
k
1
M
-
p
k
A
^
c
,
k
1
M
-
p
k
+
1
⋯
A
^
c
,
k
1
M
,
(24)
B
k
2
=
A
^
c
,
k
2
1
A
^
c
,
k
2
2
⋯
A
^
c
,
k
2
p
k
+
1
A
^
c
,
k
2
2
A
^
c
,
k
2
3
⋯
A
^
c
,
k
2
p
k
+
2
⋮
⋮
⋱
⋮
A
^
c
,
k
2
M
-
p
k
A
^
c
,
k
2
M
-
p
k
+
1
⋯
A
^
c
,
k
2
M
,where M
-
p
k
>
p
k. It is easily proven that the two matrices B
k
(
1
) and B
k
(
2
) have a full rank and can be further expressed as(25)
B
k
1
=
C
c
k
,
1
ς
k
C
c
k
,
1
Δ
c
,
k
ς
k
⋯
C
c
k
,
1
Δ
c
,
k
p
k
ς
k
C
c
k
,
1
Δ
c
,
k
ς
k
C
c
k
,
1
Δ
c
,
k
2
ς
k
⋯
C
c
k
,
1
Δ
c
,
k
p
k
+
1
ς
k
⋮
⋮
⋱
⋮
C
c
k
,
1
Δ
c
,
k
M
-
p
k
-
1
ς
k
C
c
k
,
1
Δ
c
,
k
M
-
p
k
ς
k
⋯
C
c
k
,
1
Δ
c
,
k
M
-
1
ς
k
,
(26)
B
k
2
=
C
c
k
,
2
ς
k
C
c
k
,
2
Δ
c
,
k
ς
k
⋯
C
c
k
,
2
Δ
c
,
k
p
k
ς
k
C
c
k
,
2
Δ
c
,
k
ς
k
C
c
k
,
2
Δ
c
,
k
2
ς
k
⋯
C
c
k
,
2
Δ
c
,
k
p
k
+
1
ς
k
⋮
⋮
⋱
⋮
C
c
k
,
2
Δ
c
,
k
M
-
p
k
-
1
ς
k
C
c
k
,
2
Δ
c
,
k
M
-
p
k
ς
k
⋯
C
c
k
,
2
Δ
c
,
k
M
-
1
ς
k
,where C
c
k
,
1 and C
c
k
,
2 are, respectively, composed of the first and the second rows of C
c
,
k. The matrix Δ
c
,
k
=
d
i
a
g
e
-
j
2
π
d
s
i
n
θ
k
,
1
/
λ
,
…
,
e
-
j
2
π
d
s
i
n
θ
k
,
p
k
/
λ corresponding to the kth (
k
=
K
u
+
1
,
…
,
K
u
+
D
) coherent group can be extracted from Δ
c. In view of the fact that B
k
(
1
) and B
k
(
2
) have the same rotational-invariant structures, either of them can be utilized for the estimation of coherent angles. In this study, B
k
(
1
) is taken as an example. First, two rotational-invariant submatrix pairs are constructed: the first pair is B
k
,
r
1
(
1
)
=
B
k
(
1
)
1
:
M
-
p
k
-
1
,
: and B
k
,
r
2
(
1
)
=
B
k
(
1
)
2
:
M
-
p
k
,
:; the second pair is B
k
,
l
1
(
1
)
=
B
k
(
1
)
:
,
1
:
M
-
p
k
-
1 and B
k
,
l
2
(
1
)
=
B
k
(
1
)
:
,
2
:
M
-
p
k. Subsequently, the rotational invariance can be applied to the two submatrix pairs twice, which results in two groups of coherent angle estimation results θ
^
k
,
1
1
,
θ
^
k
,
2
1
,
…
,
θ
^
k
,
p
k
1 and θ
^
k
,
1
2
,
θ
^
k
,
2
2
,
…
,
θ
^
k
,
p
k
2. The final coherent angle estimation is then achieved as θ
^
k
,
1
,
θ
^
k
,
2
,
…
,
θ
^
k
,
p
k
=
θ
^
k
,
1
1
+
θ
^
k
,
1
2
/
2
,
θ
^
k
,
2
1
+
θ
^
k
,
2
2
/
2
,
…
,
θ
^
k
,
p
k
1
+
θ
^
k
,
p
k
2
/
2 that allows more accurate angle estimation than the conventional ESPRIT method along with a slight computational gain.For further coherent polarization estimation,B
k
(
1
) and B
k
(
2
) can be rewritten as(27)
B
k
1
=
C
c
k
,
1
C
c
k
,
1
Δ
c
,
k
⋮
C
c
k
,
1
Δ
c
,
k
M
-
p
k
-
1
ς
k
Δ
c
,
k
ς
k
⋯
Δ
c
,
k
p
k
ς
k
,
(28)
B
k
2
=
C
c
k
,
2
C
c
k
,
2
Δ
c
,
k
⋮
C
c
k
,
2
Δ
c
,
k
M
-
p
k
-
1
ς
k
Δ
c
,
k
ς
k
⋯
Δ
c
,
k
p
k
ς
k
.In order to determine the polarization parameters of the coherent sources, the theory of least-squares is adopted such that(29)
Δ
Q
k
=
min
⁡
B
k
1
Q
k
-
B
k
2
F
2
,where (29) is referred to as the coherent polarization equation. The derivative of Δ
Q
k with respect to the coherent polarization matrix Q
k is defined as (30)
∂
Δ
Q
k
∂
Q
k
=
-
B
k
2
T
B
k
1
-
B
k
1
T
B
k
2
+
B
k
1
T
B
k
1
Q
k
+
Q
k
T
B
k
1
T
B
k
1
.The solution to (29) is acquired by setting the equality in (30) to be zero. Thus, we have(31)
Q
k
=
B
k
1
T
B
k
1
-
1
B
k
1
T
B
k
2
=
B
k
1
†
B
k
2
.By substituting (27) and (28) into (31), Q
k can be further reformulated as (see Appendix for details)(32)
Q
k
=
C
c
k
,
1
C
c
k
,
1
Δ
c
,
k
⋮
C
c
k
,
1
Δ
c
,
k
M
-
p
k
-
1
ς
k
Δ
c
,
k
ς
k
⋯
Δ
c
,
k
p
k
ς
k
†
C
c
k
,
2
C
c
k
,
2
Δ
c
,
k
⋮
C
c
k
,
2
Δ
c
,
k
M
-
p
k
-
1
ς
k
Δ
c
,
k
ς
k
⋯
Δ
c
,
k
p
k
ς
k
=
ς
k
Δ
c
,
k
ς
k
⋯
Δ
c
,
k
p
k
ς
k
†
μ
k
,
1
μ
k
,
2
⋱
μ
k
,
p
k
ς
k
Δ
c
,
k
ς
k
⋯
Δ
c
,
k
p
k
ς
k
,where μ
k
,
i
=
-
tan
⁡
γ
k
,
i
cos
⁡
θ
k
,
i
e
j
η
k
,
i
,
i
=
1,2
,
…
,
p
k. Equation (32) indicates that the polarization information related to the kth group coherent source can be obtained from the eigenvalues of Q
k. Thus, the estimations of polarization phase difference are given by (33)
η
^
k
,
i
=
-
arg
⁡
μ
k
,
i
,
k
=
K
u
+
1
,
K
u
+
2
,
…
,
K
u
+
D
,
i
=
1,2
,
…
,
p
k
.To achieve the estimation of coherent auxiliary polarization angles, the associated angle and polarization phase differences must obey a one-to-one relationship. For this purpose, we resort to a simple pair-matching method outlined in [14]. The matching method is implemented via a simple eigenvalue-matching operation, which is effective at the cost of a negligible increase in computational cost. The estimated auxiliary polarization angles are obtained as (34)
γ
^
k
,
i
=
t
a
n
-
1
μ
k
,
i
cos
⁡
θ
k
,
i
,
k
=
K
u
+
1
,
K
u
+
2
,
…
,
K
u
+
D
,
i
=
1,2
,
…
,
p
k
.The estimation of joint angle and polarization is therefore accomplished using the proposed method under the coexistence of both uncorrelated and coherent sources. The major steps are summarized as follows.(1)
Calculate the array covariance matrixR in (10) via the sample estimation R
^
=
∑
n
=
1
N
X
(
t
n
)
X
H
(
t
n
)
/
N, where N is the snapshot number.
(2)
Based on the moduli property of the eigenvalues, the uncorrelated sources are firstly separated from the coherent sources, and the uncorrelated angle parameters are then estimated by exploiting the rotational-invariance properties according to (11), (14), and (15). Subsequently, the associated auxiliary polarization angle and the polarization phase difference are estimated by (17) and (18).
(3)
The coherent array response matrix is estimated according to (19)–(22) and is then divided into two submatrices A
^
c
,
k
(
1
) and A
^
c
,
k
(
2
). Further, two Hankel matrices B
k
(
1
) and B
k
(
2
) are constructed for “decorrelating” via (23)–(26), and the estimation of coherent angles is obtained by utilizing two rotational-invariant submatrix pairs. On the basis of the least-square theory, the estimations of coherent auxiliary polarization angle and the polarization phase difference are obtained from (29)–(34).


## 4. Discussion

To provide insights into the proposed method, its identifiability and the computational complexity are discussed in this section.


### 4.1. Identifiability

ConsiderK far-field completely polarized narrowband sources composed of K
u uncorrelated sources and D groups of K
c coherent sources impinging upon the dual-polarization ULA, as described in Section 2. For the parameter estimation of the uncorrelated sources mentioned in Section 3.1, the inequality M
-
1
>
K
u
+
D must hold true in the light of (15), thus requiring at least K
u
+
D
+
2 dual-polarization sensors. In addition, to estimate the angle and polarization parameters of the coherent sources according to Section 3.2, the dimensions of the Hankel matrices B
k
(
1
) and B
k
(
2
) defined in (23) and (24) determine the minimum number of dual-polarization sensors required for the coherent parameter estimation. Note that the inequality M
-
p
k
>
p
k
+
1 must be satisfied, such that the minimum number of the dual-polarization sensors required for the coherent sources is max
⁡
2
p
1
+
1,2
p
2
+
1
,
…
,
2
p
D
+
1. Based on the above analysis, it is clear that the proposed method necessitates at least M
=
max
⁡
K
u
+
D
+
2
,
max
⁡
2
p
1
+
1,2
p
2
+
1
,
…
,
2
p
D
+
1 dual-polarization sensors to resolve all the incident sources, which implies that the proposed method displays potential to estimate more sources than the number of sensors.


### 4.2. Computational Complexity

Unlike the IPAS method [21], the proposed method distinguishes the uncorrelated sources from the coherent sources by directly utilizing the modulus property of eigenvalues without resorting to the extra operations, such as use of oblique projection and spatial difference matrices; thus the computational complexity of the proposed method is reduced. The major computational load of the proposed method and the IPAS method is to perform the EVD. The EVD requires about O
M
3 computations for the uncorrelated sources and O
p
k
+
1
3 for the coherent sources, which is relatively low as compared with the requirement for IPAS method (O
M
3 for uncorrelated sources and O
M
3 for coherent sources). For the existing “decorrelation” methods, such as PS-MUSIC, PDS-MUSIC, and PAS methods, a computationally intensive spectral search is involved; thus the computational complexities of these methods are relative high, especially for the finer spectral search. In summary, the proposed method offers a significant advantage in terms of computational efficiency.


## 4.1. Identifiability

ConsiderK far-field completely polarized narrowband sources composed of K
u uncorrelated sources and D groups of K
c coherent sources impinging upon the dual-polarization ULA, as described in Section 2. For the parameter estimation of the uncorrelated sources mentioned in Section 3.1, the inequality M
-
1
>
K
u
+
D must hold true in the light of (15), thus requiring at least K
u
+
D
+
2 dual-polarization sensors. In addition, to estimate the angle and polarization parameters of the coherent sources according to Section 3.2, the dimensions of the Hankel matrices B
k
(
1
) and B
k
(
2
) defined in (23) and (24) determine the minimum number of dual-polarization sensors required for the coherent parameter estimation. Note that the inequality M
-
p
k
>
p
k
+
1 must be satisfied, such that the minimum number of the dual-polarization sensors required for the coherent sources is max
⁡
2
p
1
+
1,2
p
2
+
1
,
…
,
2
p
D
+
1. Based on the above analysis, it is clear that the proposed method necessitates at least M
=
max
⁡
K
u
+
D
+
2
,
max
⁡
2
p
1
+
1,2
p
2
+
1
,
…
,
2
p
D
+
1 dual-polarization sensors to resolve all the incident sources, which implies that the proposed method displays potential to estimate more sources than the number of sensors.


## 4.2. Computational Complexity

Unlike the IPAS method [21], the proposed method distinguishes the uncorrelated sources from the coherent sources by directly utilizing the modulus property of eigenvalues without resorting to the extra operations, such as use of oblique projection and spatial difference matrices; thus the computational complexity of the proposed method is reduced. The major computational load of the proposed method and the IPAS method is to perform the EVD. The EVD requires about O
M
3 computations for the uncorrelated sources and O
p
k
+
1
3 for the coherent sources, which is relatively low as compared with the requirement for IPAS method (O
M
3 for uncorrelated sources and O
M
3 for coherent sources). For the existing “decorrelation” methods, such as PS-MUSIC, PDS-MUSIC, and PAS methods, a computationally intensive spectral search is involved; thus the computational complexities of these methods are relative high, especially for the finer spectral search. In summary, the proposed method offers a significant advantage in terms of computational efficiency.


## 5. Simulation Results

In this section, several simulations are presented to illustrate the performance of the proposed method in terms of angle and polarization estimation, where the PAS [20], IPAS [21], PS-MUSIC [17], PDS-MUSIC [18], and the well-known polarized MUSIC methods [9] are selected for comparative characterization.In the first simulation, we illustrate the effectiveness of the proposed method in distinguishing the uncorrelated sources from the coherent sources and in estimating the joint angle and polarization. A 12-sensor dual-polarization ULA is utilized to this effect. Assume that five far-field completely polarized narrowband electromagnetic wave sources, comprising the two uncorrelated sources and a group of three coherent sources, impinge on this ULA. The uncorrelated sources are parameterized by67.3
°
,
27
°
,
14
° and 42.9
°
,
19
°
,
50
°, and the coherent sources are parameterized by 25.7
°
,
40
°
,
16
°, -
10.1
°
,
13
°
,
30
°, and 15.4
°
,
23
°
,
82
° with the fading coefficients [
1
,
-
0.5280
+
0.6010
j
,
0.9335
-
0.3585
j
]. The SNR and the snapshot number are, respectively, set to be 20 dB and 500. Figure 2 depicts the moduli of eigenvalues for both uncorrelated and coherent sources. The scatter plots of the uncorrelated and coherent estimations with 100 independent trials are, respectively, shown in Figures 3 and 4.Figure 2
Moduli of the eigenvalues.Figure 3
Scatter plot of the uncorrelated sources: (a) global figure; (b) enlarged local scatter plot for the uncorrelated source 1; (c) enlarged local scatter plot for uncorrelated source 2.
(a)
(b)
(c)Figure 4
Scatter plot of the coherent sources. (a) Global figure; (b), (c), and (d) display the enlarged local scatter plots for coherent sources 1, 2, and 3, respectively.
(a)
(b)
(c)
(d)It can be clearly observed in Figure2 that the moduli of the eigenvalues associated with the uncorrelated sources are close to 1, while that associated with the coherent group is significantly away from 1. Thus, uncorrelated sources can be effectively distinguished from the coherent sources on the basis of this modulus property. The results in Figures 3 and 4 demonstrate that the proposed method can accurately estimate the angle and polarization parameters for a mixture of uncorrelated and coherent sources.In order to evaluate the angle and polarization estimation performance of the proposed method, 200 independent Monte Carlo trials are performed, and the root mean squared error (RMSE) is chosen as a performance index, which is defined as(35)
R
M
S
E
=
1
200
K
~
∑
n
=
1
200
∑
k
=
1
K
~
ω
^
n
,
k
-
ω
n
,
k
2
,where ω
^
n
,
k is the estimate of angle or polarization parameter ω
n
,
k for the kth Monte Carlo trial and K
~ denotes the number of uncorrelated or coherent sources.The second simulation studies the performance of the proposed method in estimating the angle and polarization parameters for both the uncorrelated and coherent sources using an 8-sensor dual-polarization ULA. The uncorrelated sources are parameterized by82.8
°
,
27
°
,
40
° and 56.4
°
,
9
°
,
78
°, and the two coherent sources are parameterized by 31.7
°
,
30
°
,
16
° and 8.0
°
,
13
°
,
30
° with the fading coefficients [
1,0.4469
-
0.7696
j
]. Figure 5 shows that the proposed method can effectively estimate the parameters of the uncorrelated and the coherent sources, and the accuracy of the proposed method tends to improve with an increase of SNR or number of snapshots.Figure 5
RMSE of angle and polarization parameter estimation versus SNR and snapshot number: (a) RMSE ofθ versus SNR with the fixed snapshot number 500; (b) RMSE of θ versus snapshot number with the fixed SNR 20 dB; (c) RMSE of γ versus SNR with the fixed snapshot number 500; (d) RMSE of γ versus snapshot number with the fixed SNR 20 dB; (e) RMSE of η versus SNR with the fixed snapshot number 500; (f) RMSE of η versus snapshot number with the fixed SNR 20 dB.
(a)
(b)
(c)
(d)
(e)
(f)The third simulation compares the estimation performance of the proposed method with that of the PAS and the IPAS methods. An 8-sensor dual-polarization ULA is utilized for the proposed method, and an L-shape array composed of eight 6-component electromagnetic vector sensors is used for the comparative study. The antenna hardware cost of the proposed method is less than that of the comparative methods. One uncorrelated source is parameterized by70.1
°
,
15
°
,
-
20
°, and the two coherent sources are parameterized by 20.7
°
,
30
°
,
16
° and 41.6
°
,
13
°
,
50
° with the fading coefficients [
1
,
-
0.3358
-
0.7261
j
]. Due to the fact that the PAS and the IPAS methods fail to provide an estimation of polarization parameters, only the RMSE of the angle estimates are considered in this simulation. It can be observed from Figure 6 that the proposed and the IPAS methods outperform the PAS method significantly for both the uncorrelated and the coherent sources. Moreover, the performance of the proposed method is superior for the uncorrelated angle estimation and slightly inferior for the coherent angle estimation as compared to the IPAS method. The reason for this superiority is that both the proposed method and the IPAS method estimate the uncorrelated and coherent sources separately. This allows full utilization of the effective array aperture and improves the estimation accuracy accordingly, while the PAS method estimates the uncorrelated and the coherent sources simultaneously with the whole arrays. In addition, the IPAS method estimates the coherent sources by taking an average of the received data from the 6-component vector sensor array, thus acquiring a high accuracy of coherent angle estimations at the expense of the increasing antenna hardware costs in comparison with the dual-polarization vector sensor.Figure 6
Comparison of RMSE of angle estimation of the proposed method, PAS method, and IPAS method versus SNR and snapshot number: (a) RMSE of uncorrelated angle estimation versus SNR with the fixed snapshot number 500; (b) RMSE of coherent angle estimation versus SNR with the fixed snapshot number 500; (c) RMSE of uncorrelated angle estimation versus snapshot number with the fixed SNR 20 dB; (d) RMSE of coherent angle estimation versus snapshot number with the fixed SNR 20 dB.
(a)
(b)
(c)
(d)The fourth simulation compares the estimation performance of the proposed method, the PS-MUSIC method, and the PDS-MUSIC method. The arrays used in this simulation are the same as that in the third simulation. Since the PS-MUSIC and the PDS-MUSIC methods cannot address the coexistence of the uncorrelated and coherent sources, only the RMSE of coherent angle estimates are considered in this simulation. Two coherent sources are parameterized by15.7
°
,
30
°
,
16
° and 65.1
°
,
13
°
,
30
° with the fading coefficients [
1,0.4956
+
0.4944
j
] considered in this simulation. It can be seen from Figure 7 that the proposed method outperforms PS-MUSIC and the PDS-MUSIC methods, especially when the SNR is low or the snapshot number is small. The reason is that two rotational-invariant submatrix pairs are extracted from two Hankel matrices, which can provide accurate coherent angle estimates. Restricted by the array model and the method itself, the PDS-MUSIC can estimate at most 3 sources. Moreover, the two comparative methods are coupled with MUSIC method that requires the computationally demanding spectral search.Figure 7
Comparison of RMSE of angle estimation of the proposed, PS-MUSIC, and PDS-MUSIC methods versus SNR and snapshot number: (a) RMSE versus SNR with the fixed snapshot number 500; (b) RMSE versus snapshot number with the fixed SNR 20 dB.
(a)
(b)In the last simulation, we investigate the angular resolution of the proposed method as compared to that of the well-known polarized MUSIC (P-MUSIC) method [9]. The angular resolution is defined as(36)
Δ
θ
m
i
n
=
m
i
n
Δ
θ
s
.
t
.
θ
^
1
-
θ
1
≤
Δ
θ
2
θ
^
2
-
θ
2
≤
Δ
θ
2
,where Δ
θ denotes the angular separation between the two incident sources. Consider two uncorrelated sources parameterized by 57.0
°
,
15
°
,
45
° and 57.0
°
+
Δ
θ
,
85
°
,
-
68
° impinging on the 8-sensor dual-polarization ULA. Figure 8 shows the angular resolution versus SNR and snapshot number, respectively. As observed from Figure 8, the proposed method has a higher angular resolution than the well-known P-MUSIC method. Note that the P-MUSIC requires computationally intensive 3D spectral search, and the angular resolution of the P-MUSIC method is limited by the search step. This means that if the angular separation between the two sources is less than the search step, these two sources cannot be resolved. In summary, the proposed method offers a higher angular resolution as well as lower computational complexity than the P-MUSIC method.Figure 8
Angular resolution versus SNR and snapshot number: (a) RMSE versus SNR with the fixed snapshot number, 500; (b) RMSE versus snapshot number with the fixed SNR 10 dB.
(a)
(b)


## 6. Conclusion

In this paper, a computationally efficient angle and polarization estimation method is proposed under the coexistence of uncorrelated and coherent sources by using a dual-polarization vector sensor array. The uncorrelated sources are first distinguished from the coherent sources according to the modulus property of eigenvalues. The uncorrelated angles are then estimated by exploiting the rotational invariance and the associated polarization parameters are obtained from the estimated uncorrelated array response matrix. Finally, two Hankel matrices, constructed from the elements of the estimated coherent array response matrix, are used for the coherent angle estimation, and the corresponding polarization parameters are estimated by solving the least-squares solution to the coherent polarization matrix. In addition, the identifiability and the computational complexity of the proposed method are also discussed. Simulation results show that the proposed method achieves the joint estimation of angle and polarization with a high accuracy as compared with the PS, PDS, PAS, and IPAS methods. Further, the proposed method is found to be computationally efficient and has a higher angular resolution. In the future, research will be extended to the joint 2D angle and polarization estimation with the interelement spacing beyond a half-wavelength.



---

*Source: 7537160-2016-08-25.xml*