# Radiation-Enhancement Properties of an X-Band Woodpile EBG and Its Application to a Planar Antenna

Authors: Fabrizio Frezza; Lara Pajewski; Emanuele Piuzzi; Cristina Ponti; Giuseppe Schettini
Journal: International Journal of Antennas and Propagation
 (2014)

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## Abstract

A woodpile Electromagnetic Bandgap (EBG) material has been designed, by using an in-house code that implements the Fourier Modal Method (FMM). A couple of alumina-woodpile samples have been fabricated. Several results have been collected for the transmission behaviour of the woodpile and of resonators with woodpile mirrors, in a shielded anechoic chamber, by using a vector network analyzer, in the 8–12 GHz range. These new experimental data highlight interesting properties of 3D EBG resonators and suggest possible innovative applications. Comparisons of the collected results with FMM show a satisfactory agreement. An application of the EBG resonator has been considered, for gain enhancement of a microstrip antenna: an increase of about 10 dB in the broadside gain has been measured; experimental data and numerical results obtained with the commercial software HFSS show a good agreement. A comparison is presented between EBG resonator antennas and two-dimensional uniform arrays. Finally, HFSS results are provided for EBG resonator antennas working at higher frequencies or with a more selective superstrate: a gain enhancement of more than 18 dB is achieved by such antennas.


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## Body

## 1. Introduction

Electromagnetic Bandgap (EBG) [1–3] structures, also called electromagnetic crystals, are subject to an increasing interest for their desirable properties that cannot be observed in natural materials. In this regard, they are classified as metamaterials [4].The woodpile is an EBG that may present complete three-dimensional (3D) stop bands [5, 6]. It is a stack of dielectric rods with alternating orthogonal orientations and its main advantage, compared to other geometries promoting the existence of complete bandgaps, is that it can be quite easily fabricated even for high-frequency applications. A woodpile can be realized as a sequence of layers, deposited and patterned by lithographic techniques developed for the semiconductor electronics industry [7], or by the extrusion freeforming technique [8]. Woodpile crystals with a complete band-gap centred at 2.35 μm [9] and 1.55 μm [10] have been realized through silicon double inversion of polymer templates and direct laser writing. This kind of EBG has been employed to realize waveguides [11, 12], waveguide bends [11–14], power dividers [13, 14], and as substrate [15] or superstrate [16] for the improvement of planar antenna performances.The introduction of a defect in a crystal interrupts its periodicity and may cause the occurrence of a transmission peak in a stop band: for this reason, EBGs with defects are employed in the design of resonant cavities, filters, switches, and more [17, 18]. A Fabry-Perot cavity with identical EBG mirrors can be considered as a crystal with a twin defect, that is, with a break of its periodicity obtained by a removal of one or more layers of elementary cells, such that one half of the resulting structure is a mirror image of the other one.In [19], the reflection properties of a photonic crystal with square-section rods, with and without a planar defect, were studied numerically and experimentally; the presented reflection-phase measurements of photonic crystals were the first reported in the scientific literature. In [20], a Fabry-Perot resonator with one-dimensional photonic band-gap mirrors was analyzed: the authors focused on the case of a structure with a couple of two-layer periodic mirrors surrounding a homogeneous layer, explaining the influence of design parameters on the position and tunability of defect modes; experimental results, obtained through time-domain terahertz spectroscopy, were published in [21]. The transmission properties of cavities with two-dimensional EBG mirrors were theoretically and numerically studied in [22], where the effects of the variation of physical and geometrical parameters were investigated and the application of the considered structures as filters was discussed. Experimental works at microwave frequencies on EBG cavities are not frequent, and in most of the published papers numerical results of simulations are reported.An application of the Fabry-Perot cavity with EBG mirrors is the EBG resonator antenna. In this kind of antenna, an electromagnetic crystal is employed as a superstrate on a primary radiator, backed with a ground plane, and its main effect is a considerable increase in the directivity [3, 16, 23–25]. The EBG resonator antenna appears to be an alternative to aperture antennas, as parabolic antennas or lenses, or to antenna arrays, since it does not present some problems inherent to the usual directive systems, such as the size of the focal structures, or the limitations or complications induced by the feeding circuit of arrays. The superstrate of an EBG resonator antenna has to be placed at a distance equal to an integer multiple of half a wavelength from a source backed with a ground plane, or from a radiating aperture. The forward radiation is remarkably enhanced by means of in-phase multiple reflections. Various configurations were proposed in the literature, with a microstrip patch [16, 24], slots [16], a rectangular [8] or circular [25] waveguide feed, or else a conical horn [8], as primary radiator. Even if the single-feed case is the most studied, allowing the gain to be increased with low complexity, also arrays of microstrip patches or horns were considered as sources of EBG resonator antennas [8]. Systems operating at different frequencies, ranging from the microwave region to millimeter waves, were studied. EBGs with one, two, or three periodicity directions were used as superstrates.Instead of using a ground-plane and an EBG superstrate, it is possible to put a source inside a Fabry-Perot cavity [26, 27]. Moreover, a Fabry-Perot cavity can be adopted as a cover instead of a single EBG superstrate [8, 28].Sectoral horn antennas made of woodpile material have also been studied. In this kind of antennas, the electromagnetic confinement mechanism within the horn relies wholly on the 3D EBG, which is flared in one principal plane; the antenna shows a typical sectoral horn pattern, with a directional beam in one principal plane and a broader beam in the other [29]. Linear arrays of woodpile-EBG sectoral horn antennas have been studied in [30].This work focuses on woodpile-EBG resonators and on woodpile-EBG resonator antennas. Several novel results of experiments and simulations are presented.First of all, we resume the synthesis of a woodpile EBG with a complete band-gap centred onf
=
12 GHz and extending over almost 4 GHz (Section 2). This design was performed by using an in-house code that implements the Fourier Modal Method (FMM) [31–34]. A couple of woodpile samples were fabricated, by means of alumina rods with square cross section, as briefly described in Section 3.In a shielded anechoic chamber, in the 8–12 GHz frequency range, we measured the transmission properties of our woodpile samples and of EBG Fabry-Perot cavities with different lengths and orientation of the mirrors. As already mentioned, experiments at microwave frequencies on EBG cavities have rarely been published, in most of the scientific papers only results of simulations are presented. We collected new interesting experimental results, which are reported and commented on in Sections4.1 and 4.2. We carried out comparisons of experimental data with FMM results, achieving a good agreement. Moreover, we performed simulations of EBG cavities different from the measured prototypes: the obtained results are useful to highlight some interesting properties of cavities with 3D periodic mirrors and suggest possible innovative applications of this kind of structures.Subsequently, we applied the EBG resonators to achieve gain enhancement of planar antennas; see Section4.3. By putting a woodpile sample at various appropriate distances from a printed rectangular patch antenna, we obtained an enlargement of the equivalent-aperture area of the antenna, resulting in high-gain radiation. The return loss, the gain, and the radiation pattern in the E- and H-planes were measured for the woodpile-covered microstrip antenna, changing the orientation of the EBG and its distance from the antenna. The increase in broadside gain was about 10 dB. We performed comparisons with the commercial software Ansoft HFSS, with satisfactory agreement. We also performed a comparison with the gain-enhancement properties of two-dimensional uniform arrays. Finally, by using HFSS we simulated a woodpile-covered antenna working at a higher frequency, showing that a higher gain can be obtained; furthermore, we considered a configuration with a thicker superstrate, constituted by two woodpile layers, also leading to a stronger gain enhancement of more than 18 dB.The conclusions of this work and ideas for future developments are drawn in Section5.


## 2. Design of a Woodpile EBG

A woodpile was designed, by using an in-house code implementing the FMM, a full-wave approach that solves the monochromatic plane-wave scattering problem by crossed gratings. In the FMM, the simulated structure has a finite thickness in a periodicity direction and an infinite extension in the transverse plane; interruptions of periodicity can be treated; field polarization and incidence direction are arbitrary; therefore, off-plane stop-band structures can be calculated. In the FMM simulations presented in this section, the involved materials are supposed to be lossless.In Figure1 a scheme of the unit cell of a woodpile with square-section rods is given. The cross section of the woodpile inclusions may be rectangular or circular, or else air cylindrical holes may be drilled in a dielectric sample; however, a woodpile with square-section rods is often preferred, because it is easier to fabricate. Rods belonging to two consecutive layers are orthogonal, and parallel rods are half a period offset.Figure 1
Scheme of the unit cell of a woodpile with square-section rods.Our initial goal was to design a woodpile with a gap centred on 12 GHz, possibly extending over a large frequency interval.The design parameters of a woodpile unit cell with square-section rods are the dielectric relative permittivityε
r, the side-length w of the rod-section, and the periods d
x, d
y, and d
z along the three orthogonal directions of periodicity. For a given geometry of the unit cell, there are typically no gaps until the filling factor and the dielectric contrast between rods and air are increased to some threshold values; above them, one or more gaps open up, with width usually increasing monotonically with the dielectric contrast. Moreover, a stop band becomes more pronounced as the number of woodpile layers stacked in the EBG is increased. We opted for alumina bars, to achieve a high dielectric contrast with low losses and strong stop bands with a compact structure.We performed several simulations, calculating the field reflected and transmitted by different woodpile structures when a unit-amplitude monochromatic plane wave impinges from the negativez half space (assuming that z is the direction in which the crystal has a finite-thickness). The wavenumber of the incident field is k
=
2
π
/
λ, with λ being the wavelength of the electromagnetic field in air. The wavevector is k
=
α
x
^
+
β
y
^
+
γ
z
^, with α
=
k
sin
θ
cos
⁡
φ, β
=
k
sin
θ
sin
φ, and γ
=
k
cos
⁡
θ. The electric-field polarization unit vector is u
^
=
(
cos
⁡
ψ
cos
⁡
θ
cos
⁡
φ
-
sin
ψ
sin
φ
)
x
^ + (
cos
⁡
ψ
cos
⁡
θ
sin
φ
+
sin
ψ
cos
⁡
φ
)
y
^  −  cos
⁡
ψ
sin
θ
z
^. The incidence angle is denoted with θ, φ is the azimuthal angle, and ψ is the angle between the incidence plane and u
^ [32].Depending on the periods, a woodpile may exhibit stop bands at different frequencies. We verified that if a larger complete stop band is needed, a woodpile withd
x
=
d
y
=
d
z should be preferred. Thus, we focused on solutions with d
x
=
d
y
=
d; however, for practical reasons, we chose d
z
=
4
w (so that consecutive layers could be placed on each other). It is interesting to note that, with an identical spacing in the three periodicity directions, a face-centred cubic lattice would be produced [1]. Otherwise, with d
x
=
d
y
≠
d
z, the lattice is face-centred tetragonal, which can be thought of as a face-centred cubic lattice that has been stretched or compressed in a periodicity direction.We also observed that a simple woodpile-like stack, with no shift between parallel rods belonging to different layers (hence, easier to fabricate), does not produce significant bandgaps: they are smaller than in the woodpile case and not complete.We subsequently considered in more detail the behaviour of structures built with commercially available rods of size:w
=  1.80, 3.18, 6.35, or 12.70 mm. Since an EBG typically exhibits stop bands when its period is few tenths of a wavelength, we found, as expected, that the smallest and largest bars were not suitable to our purpose. The best results have been obtained with w
=
3
.
18mm and d
=
8mm. For this geometry, in Figure 2 the transmission through the woodpile, η
T, is plotted as a function of frequency f; N represents the number of unit cells stacked along z (the total number of rod layers in this periodicity direction is therefore 4
N) and the relative dielectric constant of alumina is ε
r
,
al
=
9.8. The plane wave normally impinges on the woodpile and the electric field is x-polarized, and thus both the electric and the magnetic fields are parallel to woodpile rods (for symmetry reasons and since the involved media are lossless, the same results are obtained when the polarization of the electric field is along the y-axis). A band gap centred on f
=
12 GHz is observed, extending over almost 4 GHz.Figure 2
Transmissionη
T versus frequency when w
=
3
.
18 mm, d
=
8 mm, and ε
r
,
al
=
9.8, for normal incidence and x-polarized electric field.We also studied the off-plane behaviour of the woodpile. In Figures3 and 4 the same as in Figure 2 is shown, when N
=
2, for different incidence (θ), azimuthal (ϕ), and polarization (ψ) angles. The stop band is slightly shifted with respect to the case of Figure 2; however, it reveals to be scarcely sensitive to variations of both incidence direction and field polarization.Figure 3
The same as in Figure2, when N
=
2, for different incidence (θ), azimuthal (ϕ), and polarization (ψ) angles.Figure 4
The same as in Figure3, for some other incidence, azimuthal, and polarization angles.


## 3. Prototype Fabrication

Two identical woodpile samples were realized. The diameter tolerance of the CoorsTek AD-998 alumina rods that we employed is±
3
%, their straightness is represented by a camber/length parameter ≤0.003, and the maximum twist is 2° per 30.48 cm. To obtain a woodpile enough wide, containing at the same time size and cost, we chose a length of 20 cm for the alumina rods, corresponding to 25 periods; it is almost 7 wavelengths at 10 GHz.The alignment of the rods was performed by means of a metallic structure, specifically designed, with equally spaced steel pins mounted on the four sides of an aluminum plate. Each layer of the woodpile was formed placing the rods through two opposite rows of pins, with a distanced between two consecutive rods. Once a layer was arranged, the neighbouring one was obtained by using the two orthogonal rows of pins, thus achieving a rotation of 90° among adjacent rod gratings. Rods in contact were glued together. A picture of the resulting prototype is reported in Figure 5.Figure 5
Picture of woodpile prototype.Moreover, we designed and realized a PVC table and a teflon/PVC support, to hold the woodpile samples during the experimental investigations. The scheme of the support and a picture of the woodpile prototypes on it are shown in Figure6.(a) Scheme of the teflon/PVC support. (b) The woodpile prototypes on the support.
(a)
(b)


## 4. Results

In this Section, results of our measurements and simulations are presented.All the experiments have been performed in a 3.20 m× 3.20 m × 2.70 m shielded anechoic chamber, using a HP 8530 vector network analyzer.The first series of measurements concerned the transmission properties of both a single woodpile EBG and of woodpile cavities. The adopted setup consisted of a couple ofX-band precision pyramidal horn antennas, placed one in front of the other, with the woodpile samples in the middle, held by the above described support.In order to comply with the frequency band of the horn antennas, measurements were performed in the 8–12 GHz range. The distance between the two antennas was chosen after a series of preliminary experiments aimed at ensuring a good compromise between the planarity of the wavefront impinging on the woodpile and the diffraction effects due to the finite extension of the samples.The transmission properties of the woodpile samples were determined from the measured magnitude of theS
21 scattering parameter. To this aim, a preliminary reference calibration was performed with no sample placed between the two horns. Upon completion of each experimental session a further measurement was performed removing again the samples, in order to check that the drift in the measurement system was within acceptable levels.The second series of measurements concerned the radiation properties of the EBG resonator antenna, constituted by a woodpile-covered patch. Measurements included return loss, gain, and radiation patterns in the E- and H-planes. Only for the return loss, a different vector network analyzer was used: Agilent E8363B, preliminarily calibrated at the port by means of a SOL procedure and by employing the 85052B mechanical calibration kit. Gain and radiation pattern measurements were performed with a setup similar to the one described for transmission properties characterization. The receiving horn antenna was replaced by the patch antenna, placed on a remotely controlled turntable. The distance between the two antennas was chosen to be 1 m, in order to be in the far field of the radiators. The setup was preliminarily subjected to a reference calibration with the receiving patch antenna replaced by the second standard gain horn antenna (broadside gain equal to 16 dB and standing-wave ratio equal to 1.25).


### 4.1. Woodpile EBG

We characterized experimentally our woodpile, measuring its transmission properties.In Figure7, results for η
T as a function of frequency are shown, obtained with the two prototypes juxtaposed and placed between the two precision horn antennas. It is worth citing that horn antennas have already been used in the past for the measurement of transmission through woodpile material; see Figures 3 and  4 in [16]. Our experimental curve in Figure 7 is compared with FMM results (the N
=
2 curve of Figure 2) and the agreement is good. Here and in the following, the differences between measured data and simulation results could be attributed to the fact that, in the FMM, the excitation is a monochromatic plane wave, the involved materials are supposed to be lossless, and above all the woodpile extension is infinite in the x and y directions; therefore, diffraction effects at the edges of the prototypes are neglected.Figure 7
Transmission properties of the woodpile:η
T as a function of frequency, N
=
2, measured data, and FMM results.To give an idea of the electromagnetic effect of the PVC table and teflon/PVC support,η
T has been measured when only horns were present (empty chamber) and when the table and the support, without woodpile prototypes, were positioned between the antennas: results as a function of frequency are reported in Figure 8. Moreover, in the same figure results for the transmission beyond a 20 × 20 cm2 copper plane (held on the support, placed on the table) are shown. Analysis of Figure 8 shows that the effect of the table and support is rather negligible (as compared to the woodpile effect), with variations within ±1 dB. However, the curve recorded with the copper plane (having roughly the same transversal dimensions of the woodpile samples) shows that the effect of edge diffraction is clearly visible; nonetheless, its impact on the measured transmission curves with the EBG samples should not be so important, because of the limited shielding effectiveness of the samples themselves in the stop band (transmission generally above -
15 dB, as shown in the following results).Figure 8
η
T versus frequency for the empty anechoic chamber; in the presence of the table and the support; in the presence of a 20 × 20 cm2 conducting plate held on the support, placed on the table.


### 4.2. Woodpile Cavity

We subsequently studied the electromagnetic behaviour of an EBG cavity, constituted by our woodpile prototypes placed at a distanceh from each other, as sketched in Figure 9. This is a symmetrical structure with respect to the x
y plane and it resonates when its equivalent length L
eq is an integer multiple of λ
/
2.Figure 9
Sketch of a woodpile symmetrical cavity.We placed the cavity between the horn antennas. This structure may also be considered as a woodpile with a break of its periodicity, in which some periodic layers of rods are replaced by a homogeneous air region with thicknessh in the z direction.In Figure10, the transmission η
T is reported, as a function of frequency, when h
=
60, 90, and 119mm and the inner rods of the cavity are parallel to the electric field. The figure shows that a single periodicity interruption may cause several localized states within a stop band: in fact, each curve presents various transmission peaks. In longer cavities, a higher number of resonances occurs within the same frequency range, as expected. Moreover, all the structures considered in the figure resonate at 10.3 GHz, and it is noted that the relevant peak has a higher quality factor when the cavity is longer.Figure 10
η
T versus frequency (measured results): h
=
60, 90, and 119 mm, and the electric field is parallel to the inner rods of the cavity.The experimental curve forh
=
90 mm was presented in [35], where it was compared, with good agreement, with FMM results. Let us now consider more in depth just this case. For such a cavity, three transmission peaks are observed. They are centred on f
1
≅
8
.
80 GHz, f
2
≅
10
.
30 GHz, and f
3
≅
11
.
76 GHz. At these frequencies, the wavelength in air turns out to be λ
1
≅
34
.
1 mm, λ
2
≅
29
.
1 mm, and λ
3
≅
25
.
5 mm, respectively. Then, it can be deduced that L
eq
≅
102 mm ≅
6
λ
1
/
2
≅
7
λ
2
/
2
≅
8
λ
3
/
2: this means that the equivalent length of the cavity covers the whole air region plus about half thickness of both the EBG mirrors (L
eq
≅
h
+
4
w). This result is very interesting, and the same is found if the h
=
60mm and h
=
119mm cases are examined.The equivalent length of the cavity is highly dependent on the electromagnetic field polarization with respect to the woodpile orientation. We also measured cavities having the inner rods orthogonal to the electric field. An example is given in Figure11. We verified that a resonance at 10.3 GHz, as in Figure 10, is obtained, when h
=
26, 84, and 142 mm. Analyzing the experimental results plotted in Figure 11, it turns out that when the electric field is orthogonal to the inner rods of the cavity, the equivalent length covers the whole air region plus the thickness of three periodic layers of both the mirrors (L
eq
≅
h
+
6
w).Figure 11
η
T versus frequency (measured results); h
=
26, 84, and 142 mm, and the electric field is orthogonal to the inner rods of the cavity.As a consequence, it seems that the periodic arrangement of bars perpendicular to the electric field has a negligible effect on the transmission through the whole structure. This deduction is confirmed by the FMM results shown in Figure12, where η
T is plotted, as a function of frequency, when h
=
90mm. The behaviour of three different structures is compared in this figure: the solid line refers to a two-dimensional EBG cavity obtained from the woodpile cavity relevant to Figure 10, by removing the bars orthogonal to the electric field (consequently, only bars parallel to the electric field are present); on the contrary, the dotted line refers to a cavity obtained by removing the bars parallel to the electric field (so, the remaining bars are perpendicular to the electric field); the dashed line corresponds to the reference case of woodpile cavity and it has been reported for comparison. It can be appreciated that when only rods perpendicular to the electric field are present, the transmission through the structure is almost unitary; when only rods parallel to the electric field are present, the peaks are slightly shifted with respect to the woodpile case. These results suggest that adjacent layers of a woodpile might be independently designed, to interact with different linear sources having the electric field parallel to their rods, or to modify and control the polarization of an elliptically polarized field.Figure 12
η
T versus frequency (FMM results), when h
=
90 mm and only rods parallel (solid line) or orthogonal (dotted line) to the electric field are present, or else the whole woodpile cavity is considered (dashed line).Finally, in Figure13, results are reported for h
=
99 mm and inner rods of the cavity orthogonal to the electric field. Two different curves are plotted, obtained when the electric field illuminating the cavity was perpendicular to the ceiling and the floor, or to the side walls, of the anechoic chamber. This figure gives an idea of the anechoicity of our environment and of the reliability of our measurements. The frequency behaviour of η
T is qualitatively the same for both curves. It is important to notice that the resonances are coincident: this means that they are revealed with good accuracy in our experimental setup.Figure 13
η
T versus frequency (measured results); h
=
99 mm and the electric field is orthogonal to the inner rods of the cavity. The reported results have been obtained with the electric field orthogonal to the ceiling and the floor (full line), or to the side walls (dotted line), of the anechoic chamber.


### 4.3. Gain Enhancement of a Microstrip Antenna

An interesting and promising application of EBG resonators is their use for antenna-gain enhancement, as discussed in Section1.According to the image theory, a configuration equivalent to the cavity of Figure9 is obtained, if it is halved with respect to its symmetry plane with a perfectly conducting surface. If the ground plane of a patch antenna is employed as the perfectly conducting surface, the compound radiator sketched in Figure 14 is obtained.Figure 14
Sketch of the patch antenna with the woodpile superstrate.In previous works, we already simulated radiators made of a microstrip antenna with a woodpile superstrate [33, 34]. We presented preliminary experimental results for a woodpile-covered microstrip antenna in [35]. In this subsection, we report and comment on several new results of both experiments and simulations, concerning a woodpile-covered microstrip rectangular patch. In [16], a structure similar to the one considered here is studied: it is a microstrip rectangular patch with a woodpile superstrate and few measured results are given, at 12.47 GHz, for the return loss, the gain, and the radiation patterns in E- and H-planes.The microstrip antenna used in this work was realized from a 0.76 mm thick Rogers/RT Duroid 5870 layer (relative permittivity 2.33), printed on both sides with 36μm thick copper. With a PC-controlled milling table, on one side of the layer a 8 mm × 8.4 mm rectangular patch was cut. The antenna is fed from below by a coaxial probe (SMA connector): the feed point, where the probe is attached to the patch, is centred with respect to the shorter side of the patch and it is 1.2 mm away from the centre of the longer side. This antenna has been designed to work in X-band, to comply with the operating band of our precision horn antennas. Measurements of the return loss of the patch antenna revealed that it resonates at 10.3 GHz. At this frequency, the magnitude of the return loss is -
11
.
69 dB and the broadside gain is 6.18 dB.We characterized our woodpile-covered patch antenna by positioning the superstrate at various distances from the antenna, corresponding to half length (h
/
2) of cavities resonating at 10.3 GHz. At such distances, we first studied how the EBG affects the antenna matching. In Figure 15, the magnitude of the measured scattering parameter S
11 is plotted, as a function of frequency, for the patch antenna alone. In Figure 16, the same as in Figure 15 is reported for the woodpile-covered patch, for different values of h; the bars nearest to the patch are parallel to the electric field. It can be appreciated that the presence of the EBG superstrate does not significantly change the frequency behaviour of the return loss.Figure 15
Return loss versus frequency for the rectangular microstrip antenna.Figure 16
Return loss of the woodpile-covered patch antenna, versus frequency. Four different distances (h
/
2) between patch and woodpile are considered. The woodpile rods nearest to the ground plane are parallel to the electric field radiated by the patch.We verified that achieving a good parallelism between the ground-plane and the woodpile is very important to maximize the performances of the compound antenna. Moreover, we observed that a woodpile shift, parallel to the ground plane, does not affect the behaviour of the radiator. The orientation of the superstrate, instead, is very important, as in woodpile cavities.In Figure17, the broadside gain of the woodpile-covered patch antenna, G
pw, normalized to the broadside gain of the patch alone, G
p, is plotted as a function of frequency for the same woodpile orientation and h values studied in Figure 16. The broadside gain enhancement due to the woodpile occurs at 10.3 GHz, when the structure is matched and the equivalent distance between the woodpile and the patch is roughly equal to an integer multiple of λ
/
2: multiple reflections are present between the antenna and the superstrate, and they are summed in phase at the interface between air and woodpile.Figure 17
Broadside gain of the woodpile-covered patch antenna,G
pw, normalized to the broadside gain of the patch alone, G
p, in dB, versus frequency; h assumes different values, and the woodpile bars nearest to the ground plane are parallel to the electric field radiated by the patch.In Figure18, G
pw normalized to G
p is reported, as a function of frequency, for the h
=
90mm case; the experimental curve is compared with results obtained by using the commercial software Ansoft HFSS, implementing the finite element method, and the agreement is quite satisfactory. The experimental results show that a gain enhancement of 10.21 dB occurs at 10.3 GHz, due to the EBG; the calculated gain enhancement turns out to be slightly higher; it is 11.06 dB. In Table 1, the measured values of both G
p and G
pw can be found, for different frequencies.Table 1
Measured gain of the patch alone and of the woodpile-covered patch, in the 8–12 GHz range (h
/
2
=
45 mm).
f (GHz)
G
p (dB)
G
pw (dB)
8
−3.88
−5.96
8.5
0.09
−9.49
9
1.47
−4.11
9.5
1.85
−0.29
10
4.61
7.02
10.3
6.18
16.39
10.5
5.43
5.42
11
1.52
4.39
11.5
1.68
−16.72
12
1.24
−4.63
Results for the resonance frequency of the antenna, that is, 10.3 GHz, are reported in bold.Figure 18
G
pw normalized to G
p, in dB, versus frequency; the distance between patch and EBG is h
/
2
=
45 mm and the woodpile bars nearest to the patch are parallel to the electric field.In Figure19, the measured E- and H-plane radiation patterns (dB) of the woodpile-covered patch antenna, normalized to their maximum values, are presented for the same case considered in Figure 18. Results for the patch alone are also reported, for comparison. The directivity enhancement due to the woodpile is strongly evident in the radiation patterns of Figure 19. For the EBG-covered antenna, the measured Half-Power Beamwidth (HPBW) is 12° in the E-plane and 14° in the H-plane; the Side-Lobe Level (SLL) is -
9
.
84 dB in the E-plane and -
13
.
15 dB in the H-plane. The experimental curves of Figure 19 are compared with the results obtained by using the HFSS software: it can be noted that the agreement is good and that the SLL predicted by HFSS is lower than the measured one in both the E- and H-planes.Figure 19
E- and H-plane radiation patterns (dB) of the woodpile-covered patch antenna, normalized to its maximum value;h
/
2
=
45 mm, and the bars nearest to the patch are parallel to the electric field. Experimental results for the patch and curves obtained by using HFSS are reported, for comparison.In Figure20, the measured H-plane radiation pattern is plotted for two different values of the distance between the EBG and the microstrip antenna: in particular, the case h
/
2
=
45mm, already shown in Figure 19, is compared with the case h
/
2
=
74 mm. In both configurations the woodpile bars nearest to the patch are parallel to the electric field. It can be appreciated that, when the distance between patch and woodpile is larger, the main beam is narrower and the side-lobe level is higher. This is coherent with the results of Figure 10, where larger cavities show narrower resonance peaks.Figure 20
H-plane radiation pattern (dB) of the woodpile-covered patch antenna, normalized to its maximum value, whenh
/
2
=
45 and 74 mm. The bars nearest to the patch are parallel to the electric field.It is interesting to perform a comparison between the gain enhancement obtained with the woodpile superstrate and the one that could be achieved with a two-dimensional array of patches occupying the same geometrical area as the woodpile. In Table2, we report numerical results calculated for a uniform two-dimensional array with N
a elements. The maximum area that the array can cover is a square equal to the woodpile extension: 20 × 20 cm2. Consequently, once N
a is fixed, the array spacing cannot be larger than 20
/
(
N
a
-
1
) cm (second column). If the spacing specified in the third column of the table is chosen (giving the best results for the array with N
a elements), at 10.3 GHz the area of the array turns out to be the one given in the fourth column; the corresponding gain enhancement is reported in the fifth column of the table.Table 2
Gain enhancement obtained by using a two-dimensional uniform array withN
a elements.
N
a
Max spacing
Opt spacing
Area (cm2)
Δ
G (dB)
4
6.87λ
0.640λ
1.86
×
1.86
8.90
9
3.43λ
0.740λ
4.31
×
4.31
13.56
25
1.72λ
0.900λ
10.5
×
10.5
19.00
49
1.14λ
0.880λ
15.4
×
15.4
22.30
81
0.858λ
0.858λ
20.0
×
20.0
23.98It is observed that, with a 9-element array, covering a fraction of the available area, a gain enhancement equal to 13.56 dB can be obtained. This value is slightly higher than the one expected for the woodpile-covered patch (we recall that the gain enhancement calculated by using HFSS is 11.06 dB whenh
=
90 mm). If an array with a higher number of elements is considered, a stronger gain enhancement can be achieved; when 81 elements are present, the whole woodpile area is occupied and the gain enhancement is about 24 dB.These results show that, when a directive beam is needed, a woodpile cover can be considered a good alternative to an array not in the sense that it gives a higher increase of the gain. One of the benefits of the EBG resonator antenna resides in the possibility of obtaining a high gain with a device that uses a single feed, without the complications and limitations of a multiple-source radiating system. Moreover, as previously discussed, the matching of the antenna is slightly affected by the introduction of the periodic cover, while an array has a highly resonant matching.We now present new results of FMM and HFSS simulations, suggesting that if the woodpile is used to cover a patch that resonates at higher frequencies, a stronger gain enhancement is obtained. Another possibility that we investigate, aiming at improving the gain enhancement, is the introduction of a superstrate with a higher number of periodic layers.In Figure21, FMM results are reported for a Fabry-Perot cavity with woodpile mirrors at a distance h
=
90mm. The mirrors are constituted by one or two woodpile layers. The transmission through the cavity is plotted as a function of frequency in the 8–16 GHz range. It is observed that with two woodpile layers the transmission peaks are sharper and slightly shifted toward higher or lower frequencies (they can be easily retuned to the desired frequency by changing the cavity length). In particular, if the peak near 10 GHz is considered, it has a quality factor Q
=
63.5 with a single woodpile layer and Q
=
157 in the double-woodpile case. If the peak near 11 GHz is examined, Q
=
89.5 and 687 with one and two woodpile layers, respectively. For the peak near 13 GHz, the quality factor is Q
=
93.9 and 938 with one and two woodpile layers, respectively. A higher quality factor of the cavity should result in a stronger gain enhancement of the corresponding EBG resonator antenna. Of course, with a double woodpile superstrate higher losses are present (we recall that in FMM simulations the involved materials are assumed to be lossless) partially cancelling the expected gain improvement.Figure 21
FMM results for a Fabry-Perot cavity with mirrors constituted by one (N
=
1, dashed line) or two (N
=
2, solid line) woodpile layers: transmission as a function of frequency.The HFSS results reported in Figures22–24 concern a woodpile-covered microstrip antenna working at 13.3 GHz. The patch is rectangular and its size is 6.2 mm × 6.3 mm. At 13.3 GHz, with the woodpile at a distance h
/
2
=
45mm, the gain enhancement due to the presence of the EBG superstrate turns out to be 14dB and the return loss of the compound radiator is less than -
20dB. In Figure 22, the return loss of the woodpile-covered antenna is plotted as a function of frequency and it is compared with the return loss of the patch alone: it can be noticed that the introduction of the superstrate has a negligible effect on the antenna matching; in particular the peak turns out to be slightly shifted toward lower frequencies. In Figure 23, the broadside gain of the woodpile-covered patch antenna, G
pw, normalized to the broadside gain of the patch alone, G
p, in dB, is plotted as a function of frequency. Furthermore, in Figure 24 we present the E- and H-plane radiation patterns for this antenna; the HPBW is 8° in the E-plane and 7° in the H-plane; the SLL is -
12
.
78 dB in the E-plane and -
15
.
55dB in the H-plane. As expected, working at a higher frequency we obtained a stronger gain enhancement and more directive radiation patterns than at 10.3 GHz.Figure 22
Return loss of the woodpile-covered patch antenna resonating at 13.3 GHz and of the patch alone, versus frequency; the distance between patch and woodpile ish
/
2
=
45 mm.Figure 23
Broadside gain of the woodpile-covered patch antenna,G
pw, normalized to the broadside gain of the patch alone, G
p, in dB, versus frequency; the structure is the same as in Figure 22.Figure 24
E- and H-plane radiation patterns for the woodpile-covered patch antenna, calculated at 13.3 GHz; the structure is the same as in Figure22.The HFSS results reported in Figures25–27 concern an EBG resonator antenna working at 13.24 GHz, made of a microstrip patch covered by a superstrate constituted by two woodpile layers. The patch is the same as in the previous example. At 13.24 GHz, with the superstrate at a distance h
/
2
=
45mm, the gain enhancement due to the presence of the EBG is 18
.
28dB and the return loss of the compound radiator is less than -
20dB. In Figure 25, the return loss of the EBG resonator antenna is plotted as a function of frequency and it is compared with the return loss of the patch alone; the matching of the patch is slightly affected by the introduction of the double-woodpile superstrate. In Figure 26, the broadside gain of the EBG resonator antenna, G
pw, normalized to the broadside gain of the patch alone, G
p, in dB, is plotted as a function of frequency; the peak of gain enhancement is higher and narrower than in Figure 23. Finally, in Figure 27 we report the E- and H-plane radiation patterns for this antenna; the HPBW is 9° in the E-plane, 9° in the H-plane; the SLL is -
16
.
99 dB in the E-plane, -
20
.
23 dB in the H-plane. These results show that the introduction of a second woodpile layer further improves the gain enhancement.Figure 25
Return loss of the patch antenna with a cover constituted by two woodpile layers, resonating at 13.24 GHz, compared with the return loss of the patch alone; the distance between patch and woodpile ish
/
2
=
45 mm.Figure 26
Broadside gain,G
pw, normalized to the broadside gain of the patch alone, G
p, in dB, versus frequency; the structure is the same as in Figure 25.Figure 27
E- and H-plane radiation patterns, calculated at 13.24 GHz; the structure is the same as in Figure25.


## 4.1. Woodpile EBG

We characterized experimentally our woodpile, measuring its transmission properties.In Figure7, results for η
T as a function of frequency are shown, obtained with the two prototypes juxtaposed and placed between the two precision horn antennas. It is worth citing that horn antennas have already been used in the past for the measurement of transmission through woodpile material; see Figures 3 and  4 in [16]. Our experimental curve in Figure 7 is compared with FMM results (the N
=
2 curve of Figure 2) and the agreement is good. Here and in the following, the differences between measured data and simulation results could be attributed to the fact that, in the FMM, the excitation is a monochromatic plane wave, the involved materials are supposed to be lossless, and above all the woodpile extension is infinite in the x and y directions; therefore, diffraction effects at the edges of the prototypes are neglected.Figure 7
Transmission properties of the woodpile:η
T as a function of frequency, N
=
2, measured data, and FMM results.To give an idea of the electromagnetic effect of the PVC table and teflon/PVC support,η
T has been measured when only horns were present (empty chamber) and when the table and the support, without woodpile prototypes, were positioned between the antennas: results as a function of frequency are reported in Figure 8. Moreover, in the same figure results for the transmission beyond a 20 × 20 cm2 copper plane (held on the support, placed on the table) are shown. Analysis of Figure 8 shows that the effect of the table and support is rather negligible (as compared to the woodpile effect), with variations within ±1 dB. However, the curve recorded with the copper plane (having roughly the same transversal dimensions of the woodpile samples) shows that the effect of edge diffraction is clearly visible; nonetheless, its impact on the measured transmission curves with the EBG samples should not be so important, because of the limited shielding effectiveness of the samples themselves in the stop band (transmission generally above -
15 dB, as shown in the following results).Figure 8
η
T versus frequency for the empty anechoic chamber; in the presence of the table and the support; in the presence of a 20 × 20 cm2 conducting plate held on the support, placed on the table.


## 4.2. Woodpile Cavity

We subsequently studied the electromagnetic behaviour of an EBG cavity, constituted by our woodpile prototypes placed at a distanceh from each other, as sketched in Figure 9. This is a symmetrical structure with respect to the x
y plane and it resonates when its equivalent length L
eq is an integer multiple of λ
/
2.Figure 9
Sketch of a woodpile symmetrical cavity.We placed the cavity between the horn antennas. This structure may also be considered as a woodpile with a break of its periodicity, in which some periodic layers of rods are replaced by a homogeneous air region with thicknessh in the z direction.In Figure10, the transmission η
T is reported, as a function of frequency, when h
=
60, 90, and 119mm and the inner rods of the cavity are parallel to the electric field. The figure shows that a single periodicity interruption may cause several localized states within a stop band: in fact, each curve presents various transmission peaks. In longer cavities, a higher number of resonances occurs within the same frequency range, as expected. Moreover, all the structures considered in the figure resonate at 10.3 GHz, and it is noted that the relevant peak has a higher quality factor when the cavity is longer.Figure 10
η
T versus frequency (measured results): h
=
60, 90, and 119 mm, and the electric field is parallel to the inner rods of the cavity.The experimental curve forh
=
90 mm was presented in [35], where it was compared, with good agreement, with FMM results. Let us now consider more in depth just this case. For such a cavity, three transmission peaks are observed. They are centred on f
1
≅
8
.
80 GHz, f
2
≅
10
.
30 GHz, and f
3
≅
11
.
76 GHz. At these frequencies, the wavelength in air turns out to be λ
1
≅
34
.
1 mm, λ
2
≅
29
.
1 mm, and λ
3
≅
25
.
5 mm, respectively. Then, it can be deduced that L
eq
≅
102 mm ≅
6
λ
1
/
2
≅
7
λ
2
/
2
≅
8
λ
3
/
2: this means that the equivalent length of the cavity covers the whole air region plus about half thickness of both the EBG mirrors (L
eq
≅
h
+
4
w). This result is very interesting, and the same is found if the h
=
60mm and h
=
119mm cases are examined.The equivalent length of the cavity is highly dependent on the electromagnetic field polarization with respect to the woodpile orientation. We also measured cavities having the inner rods orthogonal to the electric field. An example is given in Figure11. We verified that a resonance at 10.3 GHz, as in Figure 10, is obtained, when h
=
26, 84, and 142 mm. Analyzing the experimental results plotted in Figure 11, it turns out that when the electric field is orthogonal to the inner rods of the cavity, the equivalent length covers the whole air region plus the thickness of three periodic layers of both the mirrors (L
eq
≅
h
+
6
w).Figure 11
η
T versus frequency (measured results); h
=
26, 84, and 142 mm, and the electric field is orthogonal to the inner rods of the cavity.As a consequence, it seems that the periodic arrangement of bars perpendicular to the electric field has a negligible effect on the transmission through the whole structure. This deduction is confirmed by the FMM results shown in Figure12, where η
T is plotted, as a function of frequency, when h
=
90mm. The behaviour of three different structures is compared in this figure: the solid line refers to a two-dimensional EBG cavity obtained from the woodpile cavity relevant to Figure 10, by removing the bars orthogonal to the electric field (consequently, only bars parallel to the electric field are present); on the contrary, the dotted line refers to a cavity obtained by removing the bars parallel to the electric field (so, the remaining bars are perpendicular to the electric field); the dashed line corresponds to the reference case of woodpile cavity and it has been reported for comparison. It can be appreciated that when only rods perpendicular to the electric field are present, the transmission through the structure is almost unitary; when only rods parallel to the electric field are present, the peaks are slightly shifted with respect to the woodpile case. These results suggest that adjacent layers of a woodpile might be independently designed, to interact with different linear sources having the electric field parallel to their rods, or to modify and control the polarization of an elliptically polarized field.Figure 12
η
T versus frequency (FMM results), when h
=
90 mm and only rods parallel (solid line) or orthogonal (dotted line) to the electric field are present, or else the whole woodpile cavity is considered (dashed line).Finally, in Figure13, results are reported for h
=
99 mm and inner rods of the cavity orthogonal to the electric field. Two different curves are plotted, obtained when the electric field illuminating the cavity was perpendicular to the ceiling and the floor, or to the side walls, of the anechoic chamber. This figure gives an idea of the anechoicity of our environment and of the reliability of our measurements. The frequency behaviour of η
T is qualitatively the same for both curves. It is important to notice that the resonances are coincident: this means that they are revealed with good accuracy in our experimental setup.Figure 13
η
T versus frequency (measured results); h
=
99 mm and the electric field is orthogonal to the inner rods of the cavity. The reported results have been obtained with the electric field orthogonal to the ceiling and the floor (full line), or to the side walls (dotted line), of the anechoic chamber.


## 4.3. Gain Enhancement of a Microstrip Antenna

An interesting and promising application of EBG resonators is their use for antenna-gain enhancement, as discussed in Section1.According to the image theory, a configuration equivalent to the cavity of Figure9 is obtained, if it is halved with respect to its symmetry plane with a perfectly conducting surface. If the ground plane of a patch antenna is employed as the perfectly conducting surface, the compound radiator sketched in Figure 14 is obtained.Figure 14
Sketch of the patch antenna with the woodpile superstrate.In previous works, we already simulated radiators made of a microstrip antenna with a woodpile superstrate [33, 34]. We presented preliminary experimental results for a woodpile-covered microstrip antenna in [35]. In this subsection, we report and comment on several new results of both experiments and simulations, concerning a woodpile-covered microstrip rectangular patch. In [16], a structure similar to the one considered here is studied: it is a microstrip rectangular patch with a woodpile superstrate and few measured results are given, at 12.47 GHz, for the return loss, the gain, and the radiation patterns in E- and H-planes.The microstrip antenna used in this work was realized from a 0.76 mm thick Rogers/RT Duroid 5870 layer (relative permittivity 2.33), printed on both sides with 36μm thick copper. With a PC-controlled milling table, on one side of the layer a 8 mm × 8.4 mm rectangular patch was cut. The antenna is fed from below by a coaxial probe (SMA connector): the feed point, where the probe is attached to the patch, is centred with respect to the shorter side of the patch and it is 1.2 mm away from the centre of the longer side. This antenna has been designed to work in X-band, to comply with the operating band of our precision horn antennas. Measurements of the return loss of the patch antenna revealed that it resonates at 10.3 GHz. At this frequency, the magnitude of the return loss is -
11
.
69 dB and the broadside gain is 6.18 dB.We characterized our woodpile-covered patch antenna by positioning the superstrate at various distances from the antenna, corresponding to half length (h
/
2) of cavities resonating at 10.3 GHz. At such distances, we first studied how the EBG affects the antenna matching. In Figure 15, the magnitude of the measured scattering parameter S
11 is plotted, as a function of frequency, for the patch antenna alone. In Figure 16, the same as in Figure 15 is reported for the woodpile-covered patch, for different values of h; the bars nearest to the patch are parallel to the electric field. It can be appreciated that the presence of the EBG superstrate does not significantly change the frequency behaviour of the return loss.Figure 15
Return loss versus frequency for the rectangular microstrip antenna.Figure 16
Return loss of the woodpile-covered patch antenna, versus frequency. Four different distances (h
/
2) between patch and woodpile are considered. The woodpile rods nearest to the ground plane are parallel to the electric field radiated by the patch.We verified that achieving a good parallelism between the ground-plane and the woodpile is very important to maximize the performances of the compound antenna. Moreover, we observed that a woodpile shift, parallel to the ground plane, does not affect the behaviour of the radiator. The orientation of the superstrate, instead, is very important, as in woodpile cavities.In Figure17, the broadside gain of the woodpile-covered patch antenna, G
pw, normalized to the broadside gain of the patch alone, G
p, is plotted as a function of frequency for the same woodpile orientation and h values studied in Figure 16. The broadside gain enhancement due to the woodpile occurs at 10.3 GHz, when the structure is matched and the equivalent distance between the woodpile and the patch is roughly equal to an integer multiple of λ
/
2: multiple reflections are present between the antenna and the superstrate, and they are summed in phase at the interface between air and woodpile.Figure 17
Broadside gain of the woodpile-covered patch antenna,G
pw, normalized to the broadside gain of the patch alone, G
p, in dB, versus frequency; h assumes different values, and the woodpile bars nearest to the ground plane are parallel to the electric field radiated by the patch.In Figure18, G
pw normalized to G
p is reported, as a function of frequency, for the h
=
90mm case; the experimental curve is compared with results obtained by using the commercial software Ansoft HFSS, implementing the finite element method, and the agreement is quite satisfactory. The experimental results show that a gain enhancement of 10.21 dB occurs at 10.3 GHz, due to the EBG; the calculated gain enhancement turns out to be slightly higher; it is 11.06 dB. In Table 1, the measured values of both G
p and G
pw can be found, for different frequencies.Table 1
Measured gain of the patch alone and of the woodpile-covered patch, in the 8–12 GHz range (h
/
2
=
45 mm).
f (GHz)
G
p (dB)
G
pw (dB)
8
−3.88
−5.96
8.5
0.09
−9.49
9
1.47
−4.11
9.5
1.85
−0.29
10
4.61
7.02
10.3
6.18
16.39
10.5
5.43
5.42
11
1.52
4.39
11.5
1.68
−16.72
12
1.24
−4.63
Results for the resonance frequency of the antenna, that is, 10.3 GHz, are reported in bold.Figure 18
G
pw normalized to G
p, in dB, versus frequency; the distance between patch and EBG is h
/
2
=
45 mm and the woodpile bars nearest to the patch are parallel to the electric field.In Figure19, the measured E- and H-plane radiation patterns (dB) of the woodpile-covered patch antenna, normalized to their maximum values, are presented for the same case considered in Figure 18. Results for the patch alone are also reported, for comparison. The directivity enhancement due to the woodpile is strongly evident in the radiation patterns of Figure 19. For the EBG-covered antenna, the measured Half-Power Beamwidth (HPBW) is 12° in the E-plane and 14° in the H-plane; the Side-Lobe Level (SLL) is -
9
.
84 dB in the E-plane and -
13
.
15 dB in the H-plane. The experimental curves of Figure 19 are compared with the results obtained by using the HFSS software: it can be noted that the agreement is good and that the SLL predicted by HFSS is lower than the measured one in both the E- and H-planes.Figure 19
E- and H-plane radiation patterns (dB) of the woodpile-covered patch antenna, normalized to its maximum value;h
/
2
=
45 mm, and the bars nearest to the patch are parallel to the electric field. Experimental results for the patch and curves obtained by using HFSS are reported, for comparison.In Figure20, the measured H-plane radiation pattern is plotted for two different values of the distance between the EBG and the microstrip antenna: in particular, the case h
/
2
=
45mm, already shown in Figure 19, is compared with the case h
/
2
=
74 mm. In both configurations the woodpile bars nearest to the patch are parallel to the electric field. It can be appreciated that, when the distance between patch and woodpile is larger, the main beam is narrower and the side-lobe level is higher. This is coherent with the results of Figure 10, where larger cavities show narrower resonance peaks.Figure 20
H-plane radiation pattern (dB) of the woodpile-covered patch antenna, normalized to its maximum value, whenh
/
2
=
45 and 74 mm. The bars nearest to the patch are parallel to the electric field.It is interesting to perform a comparison between the gain enhancement obtained with the woodpile superstrate and the one that could be achieved with a two-dimensional array of patches occupying the same geometrical area as the woodpile. In Table2, we report numerical results calculated for a uniform two-dimensional array with N
a elements. The maximum area that the array can cover is a square equal to the woodpile extension: 20 × 20 cm2. Consequently, once N
a is fixed, the array spacing cannot be larger than 20
/
(
N
a
-
1
) cm (second column). If the spacing specified in the third column of the table is chosen (giving the best results for the array with N
a elements), at 10.3 GHz the area of the array turns out to be the one given in the fourth column; the corresponding gain enhancement is reported in the fifth column of the table.Table 2
Gain enhancement obtained by using a two-dimensional uniform array withN
a elements.
N
a
Max spacing
Opt spacing
Area (cm2)
Δ
G (dB)
4
6.87λ
0.640λ
1.86
×
1.86
8.90
9
3.43λ
0.740λ
4.31
×
4.31
13.56
25
1.72λ
0.900λ
10.5
×
10.5
19.00
49
1.14λ
0.880λ
15.4
×
15.4
22.30
81
0.858λ
0.858λ
20.0
×
20.0
23.98It is observed that, with a 9-element array, covering a fraction of the available area, a gain enhancement equal to 13.56 dB can be obtained. This value is slightly higher than the one expected for the woodpile-covered patch (we recall that the gain enhancement calculated by using HFSS is 11.06 dB whenh
=
90 mm). If an array with a higher number of elements is considered, a stronger gain enhancement can be achieved; when 81 elements are present, the whole woodpile area is occupied and the gain enhancement is about 24 dB.These results show that, when a directive beam is needed, a woodpile cover can be considered a good alternative to an array not in the sense that it gives a higher increase of the gain. One of the benefits of the EBG resonator antenna resides in the possibility of obtaining a high gain with a device that uses a single feed, without the complications and limitations of a multiple-source radiating system. Moreover, as previously discussed, the matching of the antenna is slightly affected by the introduction of the periodic cover, while an array has a highly resonant matching.We now present new results of FMM and HFSS simulations, suggesting that if the woodpile is used to cover a patch that resonates at higher frequencies, a stronger gain enhancement is obtained. Another possibility that we investigate, aiming at improving the gain enhancement, is the introduction of a superstrate with a higher number of periodic layers.In Figure21, FMM results are reported for a Fabry-Perot cavity with woodpile mirrors at a distance h
=
90mm. The mirrors are constituted by one or two woodpile layers. The transmission through the cavity is plotted as a function of frequency in the 8–16 GHz range. It is observed that with two woodpile layers the transmission peaks are sharper and slightly shifted toward higher or lower frequencies (they can be easily retuned to the desired frequency by changing the cavity length). In particular, if the peak near 10 GHz is considered, it has a quality factor Q
=
63.5 with a single woodpile layer and Q
=
157 in the double-woodpile case. If the peak near 11 GHz is examined, Q
=
89.5 and 687 with one and two woodpile layers, respectively. For the peak near 13 GHz, the quality factor is Q
=
93.9 and 938 with one and two woodpile layers, respectively. A higher quality factor of the cavity should result in a stronger gain enhancement of the corresponding EBG resonator antenna. Of course, with a double woodpile superstrate higher losses are present (we recall that in FMM simulations the involved materials are assumed to be lossless) partially cancelling the expected gain improvement.Figure 21
FMM results for a Fabry-Perot cavity with mirrors constituted by one (N
=
1, dashed line) or two (N
=
2, solid line) woodpile layers: transmission as a function of frequency.The HFSS results reported in Figures22–24 concern a woodpile-covered microstrip antenna working at 13.3 GHz. The patch is rectangular and its size is 6.2 mm × 6.3 mm. At 13.3 GHz, with the woodpile at a distance h
/
2
=
45mm, the gain enhancement due to the presence of the EBG superstrate turns out to be 14dB and the return loss of the compound radiator is less than -
20dB. In Figure 22, the return loss of the woodpile-covered antenna is plotted as a function of frequency and it is compared with the return loss of the patch alone: it can be noticed that the introduction of the superstrate has a negligible effect on the antenna matching; in particular the peak turns out to be slightly shifted toward lower frequencies. In Figure 23, the broadside gain of the woodpile-covered patch antenna, G
pw, normalized to the broadside gain of the patch alone, G
p, in dB, is plotted as a function of frequency. Furthermore, in Figure 24 we present the E- and H-plane radiation patterns for this antenna; the HPBW is 8° in the E-plane and 7° in the H-plane; the SLL is -
12
.
78 dB in the E-plane and -
15
.
55dB in the H-plane. As expected, working at a higher frequency we obtained a stronger gain enhancement and more directive radiation patterns than at 10.3 GHz.Figure 22
Return loss of the woodpile-covered patch antenna resonating at 13.3 GHz and of the patch alone, versus frequency; the distance between patch and woodpile ish
/
2
=
45 mm.Figure 23
Broadside gain of the woodpile-covered patch antenna,G
pw, normalized to the broadside gain of the patch alone, G
p, in dB, versus frequency; the structure is the same as in Figure 22.Figure 24
E- and H-plane radiation patterns for the woodpile-covered patch antenna, calculated at 13.3 GHz; the structure is the same as in Figure22.The HFSS results reported in Figures25–27 concern an EBG resonator antenna working at 13.24 GHz, made of a microstrip patch covered by a superstrate constituted by two woodpile layers. The patch is the same as in the previous example. At 13.24 GHz, with the superstrate at a distance h
/
2
=
45mm, the gain enhancement due to the presence of the EBG is 18
.
28dB and the return loss of the compound radiator is less than -
20dB. In Figure 25, the return loss of the EBG resonator antenna is plotted as a function of frequency and it is compared with the return loss of the patch alone; the matching of the patch is slightly affected by the introduction of the double-woodpile superstrate. In Figure 26, the broadside gain of the EBG resonator antenna, G
pw, normalized to the broadside gain of the patch alone, G
p, in dB, is plotted as a function of frequency; the peak of gain enhancement is higher and narrower than in Figure 23. Finally, in Figure 27 we report the E- and H-plane radiation patterns for this antenna; the HPBW is 9° in the E-plane, 9° in the H-plane; the SLL is -
16
.
99 dB in the E-plane, -
20
.
23 dB in the H-plane. These results show that the introduction of a second woodpile layer further improves the gain enhancement.Figure 25
Return loss of the patch antenna with a cover constituted by two woodpile layers, resonating at 13.24 GHz, compared with the return loss of the patch alone; the distance between patch and woodpile ish
/
2
=
45 mm.Figure 26
Broadside gain,G
pw, normalized to the broadside gain of the patch alone, G
p, in dB, versus frequency; the structure is the same as in Figure 25.Figure 27
E- and H-plane radiation patterns, calculated at 13.24 GHz; the structure is the same as in Figure25.


## 5. Conclusions

The synthesis, realization and experimental characterization of a woodpile resonator have been presented. Its application for gain-enhancement of a microstrip patch antenna has been treated.The Electromagnetic Band-Gap (EBG) material has been designed by using an in-house code implementing the Fourier Modal Method (FMM). It shows a stop-band centred on 12 GHz, extending over a large frequency interval and scarcely sensitive to variations of both incidence direction and field polarization.Two woodpile samples have been fabricated, by means of alumina rods with square cross-section. The alignment of the rods was performed by means of a metallic structure, specifically designed, with equally spaced steel pins mounted on the four sides of an aluminum plate. A teflon/PVC support has been designed and realized, to hold the woodpile samples during the experimental investigations.The transmission properties of the woodpile samples and of woodpile resonators have been measured. The cavity length and the orientation of the EBG mirrors have been varied. Several new and interesting experimental results have been reported. All the measurements have been performed in the 8–12 GHz frequency range, in a shielded anechoic chamber, using a vector network analyzer. Comparisons have been performed with FMM, obtaining a good agreement.We have verified that the EBG cavity resonates when its equivalent length is an integer multiple of half a wavelength. Moreover, we have found that the equivalent length of the cavity is highly dependent on the electromagnetic field polarization with respect to the woodpile orientation, covering the whole length of the air region plus the thickness of two or three periodic layers of both the mirrors, when the inner rods of the cavity are parallel or orthogonal to the electric field, respectively.We have shown that the periodic arrangement of bars perpendicular to the electric field has a negligible effect on the transmission through the whole cavity. This suggests that adjacent layers of a woodpile might be independently designed, to interact with different linear sources having the electric field parallel to their rods or to modify and control the polarization of an elliptically polarized field.The return loss, the gain, and the radiation pattern in the E- and H-planes have subsequently been measured, for a rectangular patch antenna working at 10.3 GHz and covered with the woodpile. Comparisons with the commercial software HFSS show a good agreement. We have observed that, when the equivalent distance between the patch an the EBG is roughly equal to an integer multiple of half a wavelength, the periodic superstrate does not significantly affect the antenna matching; the gain of the woodpile-covered antenna results to be about 10 dB greater than the gain of the patch alone. We have also found that if the distance between antenna and EBG is larger, the radiation pattern has a narrower main beam and a higher side-lobe level.We have carried out a comparison between our EBG resonator antenna and two-dimensional uniform arrays of patches. With a 9-element array, covering an area smaller than the woodpile extension, a gain enhancement can be obtained slightly higher than the one achieved by our EBG resonator antenna. An array with a higher number of elements, occupying the whole woodpile area, shows a gain enhancement much stronger than the woodpile-covered patch. Therefore, when a directive beam is needed, a woodpile cover can be considered a good alternative to an array not in the sense that it gives a higher increase of the gain. One of the benefits of the EBG resonator antenna resides in the possibility of obtaining a high gain with a single feeding device, without the complications of a multiple-source radiating system. Moreover, the matching of the antenna turns out to be slightly affected by the introduction of the periodic cover, while an array has a highly resonant matching.By performing FMM and HFSS simulations, we have demonstrated that stronger gain enhancement can be obtained working at higher frequencies and/or using a double-woodpile cover. The gain of a rectangular patch, covered with a double woodpile layer and resonating at 13.24 GHz, results to be more than 18 dB greater than the gain of the patch alone.We think that an even higher gain might be reached by designing a modified woodpile structure, with some bars displaced and optimized to achieve a more symmetric and directive radiation pattern and a better matching. We plan to investigate this solution in the near future. We are also going to study the performances of multiple antennas, working simultaneously at different frequencies and/or with different polarizations and exploiting the same woodpile layer. Finally, as is known it is possible to obtain a highly directive antenna by embedding a source into an EBG working near its band-gap [36], thanks to the limited angular propagation allowed within the crystal: we plan to compare this kind of EBG antenna with the EBG resonator antenna.



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*Source: 729187-2014-01-21.xml*