# Novel Design of High-Gain Planar Dipole-Array Antenna for RFID 2.45 GHz

Authors: Danpeng Xie; Xueguan Liu; Huiping Guo; Xinmi Yang
Journal: International Journal of Antennas and Propagation
 (2014)

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## Abstract

This paper presents a novel high-gain planar dipole-array antenna for 2.45 GHz which consists of four planar dipole elements placed in two parallel lines. Phase retardation of each element is set by feeding network to form controllable radiation direction. The radiation pattern of the array is discussed according to Arrays Theorem. The measured −10 dB band is from 2.3 GHz to 2.57 GHz, and peak gain in this band is 7.5 dBi. The gain can even reach 10.5 dBi after installing additional ground. The proposed antenna has advantages of high gain, controllable direction, and planarity which are suitable for 2.45 GHz RFID base station.


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## Body

## 1. Introduction

As an integral part of our life, RFID increases productivity and convenience [1]. It is ubiquitous in solving problems in fields such as supply chain management, security, personal identification, and asset tracking [2]. Low-gain tag antennas are used for transponder, and a high-gain reader antenna is required to increase the reading range [3]. To meet the high-gain demand of RFID base station, antenna arrays are arranged in certain position. With certain matching condition of amplitude and phase of current for each element, the radiation vectors superpose and gain enhances according to Arrays Vector Sum Theorem [4]. Among various kinds of element structure, microstrip and dipole are popularly used to provide high gain. Microstrip antenna has characteristics of easy integration, planar structure, light weight, small size, and low profile. However, it suffers from low directivity, narrow bandwidth typically 5%, and low efficiency [5]. Dipole-printed antenna is fit for high-gain systems for its wide bandwidth and simple structure [6].Recently, a composite dipole antenna array with direct feed is discussed [7]. Efficiency and omnidirectional radiation gain are enhanced due to the load of antenna. Another novel omnidirectional antenna with bandwidth broadened is presented [8]. Two half-wavelength dipoles are printed on both sides, and the parasitical elements are connected to the fed ones by metal pins. The antenna is fed by coupled lines.In this work, a novel high-gain planar dipole-array antenna with wide bandwidth and controllable radiation direction is presented. Dipoles are printed on both sides of the substrate, and all dipoles are fed by CPW line, with advantages of low radiation loss (especially from the feed point), less dispersion, planar configuration, and amenability to integrate with active microwave devices [9, 10].


## 2. Structure of Proposed Array Antenna

Structure of proposed antenna is shown in Figure1. Figure 1(a) presents the structure of four-element arrays which is printed on a substrate with relative permittivity of 4.4, a loss tangent of 0.02, and a thickness of h
=
1
.
6
mm. Figure 1(b) presents structure of one element. Top layer contains planar coaxial feed lines, radiation dipoles, and ground. Bottom layer is ground with similar dipole structure of top layer. Two rows vias connect upper and lower ground plane. Structure of the coplanar waveguide feeding network is shown in Figure 2, which not only divides power for four ports, but also acts as a phase shifter to make 180 deg phase retardation. In this case, current of arrays has 180 deg phase retardation with the same direction. By controlling phase retardation of each array, radiation direction is identified. By setting variables l and l
e, phase retardation can be tuned using Ansoft HFSS. Table 1 lists the possible combinations of l and l
e for 180 deg phase retardation. In our design, l and l
e are selected as 60 mm and 7.2 mm.Table 1
Values ofl andl
e with 180 deg phase retardation.
l (mm)
l
e (mm)
φ (deg)
20
10.2
179.5/179.1
32
9.5
179.2/179.2
40
9
179.2/179.3
48
8.4
179.5/179.7
60
7.2
179.5/179.7Geometries of the proposed antenna. (a) Four-element arrays and (b) top layer and bottom layer of one element.
(a)
(b)Figure 2
Structure of central coplanar waveguide.


## 3. Analysis of Proposed Arrays Using Arrays Theorem

In this section, analysis of proposed arrays using Arrays Theorem is given. Firstly, two dipole elements in one line comprise a Binary Side Fire Array. The two Binary Side Fire Arrays with four elements comprise a Binary End Fire Array [11]. For Binary Side Fire Array, assuming that the array distance is half wavelength, namely, d
=
λ
/
2, and the phase difference of the two elements is φ
=
90
deg, the current relation of the two elements can be expressed as
(1)
I
2
=
I
1
e
-
j
φ
.For Binary Side Fire Array, the total far electric fieldE
θ is expressed as
(2)
E
θ
=
E
1
θ
+
E
2
θ
E
=
j
60
I
1
r
cos
(
(
π
/
2
)
cos
θ
)
sin
θ
(
e
-
j
k
Δ
k
+
I
2
I
1
e
j
k
Δ
k
)
e
-
j
k
r
E
=
j
60
I
1
r
cos
(
(
π
/
2
)
cos
θ
)
sin
θ
2
cos
(
k
d
2
cos
θ
-
φ
2
)
E
=
×
e
-
j
k
r
e
-
j
(
φ
/
2
)
.The corresponding radiation direction pattern is(3)
F
(
θ
)
=
|
E
|
E
M
=
f
(
θ
)
f
M
=
cos
(
(
π
/
2
)
cos
θ
)
sin
θ
cos
(
π
2
cos
θ
-
π
4
)
.For the Binary End Fire Array, the phase retardation of its two elements (i.e., two Binary Side Fire Arrays) isγ
=
-
90 deg, and the distance between the elements is l
=
λ
/
2. Substituting d
=
λ
/
2 and φ
=
0 deg, the total far electric field of the Binary End Fire Array E
θ is expressed as
(4)
E
θ
=
E
1
θ
+
E
2
θ
+
E
3
θ
+
E
4
θ
E
=
j
60
I
1
r
cos
(
(
π
/
2
)
cos
θ
)
sin
θ
(
e
-
j
k
(
r
+
Δ
r
)
+
I
2
I
1
e
-
j
k
(
r
-
Δ
r
)
)
E
=
×
(
e
-
j
k
(
s
+
Δ
s
)
+
I
3
I
1
e
-
j
k
(
s
-
Δ
s
)
)
E
=
j
60
I
1
r
cos
(
(
π
/
2
)
cos
θ
)
sin
θ
4
cos
(
k
d
2
cos
θ
-
φ
2
)
E
=
×
e
-
j
k
r
e
-
j
(
φ
/
2
)
cos
(
k
l
2
cos
θ
-
γ
2
)
e
-
j
k
s
e
-
j
(
γ
/
2
)
.The final radiation pattern of the four element array is calculated as(5)
F
(
θ
)
=
cos
(
(
π
/
2
)
cos
θ
)
sin
θ
cos
(
π
2
cos
θ
)
cos
(
π
2
cos
θ
+
π
4
)
.The calculated radiation pattern of the four-element array by MATLAB is shown in Figure3. Main lobe shifts towards left with side lobe towards right. So by controlling phase of each array φ and γ, radiation direction can be controlled. Hence, the proposed antenna is suitable for base station application with particular beam angle requirement.Radiation pattern of arrays calculated by MATLAB. (a) Binary Side Fire Array and (b) Binary End Fire Array.
(a)
(b)


## 4. Simulated and Measured Result

The distance of two adjacent arrays in the same rowd, length of impedance tuner on CPW line l
14, and width of impedance tuner for dipole w
4 are key parameters of the proposed antenna due to their dominant effects on the antenna resonant frequency. Figure 4(a) shows the simulated return loss and Figure 4(b) shows the simulated gain for different array distance d values with other parameters fixed. It can be concluded that decreasing array distance d enhances the total realized gain in the range from 2.3 GHz to 2.8 GHz. Distance d also controls antenna impedance matching and resonant frequency. Figure 5 shows the effect of l
14 on return loss. It can be noticed that length of impedance tuner on CPW has a remarkable effect on resonant frequency. Figure 6 shows the effect of w
4 on impedance matching.Array distanced effect on simulated return loss and simulated gain of four-element arrays without additional ground. (a) d effect on simulated return loss and (b) d effect on simulated gain.
(a)
(b)Figure 5
Length of CPW line impedance tunerl
14 effect on simulated return loss of four-element arrays without additional ground.Figure 6
Width of dipole impedance tunerw
4 effect on simulated return loss of four-element arrays without additional ground.After optimization by HFSS, main parameters of arrays with maximum gain by different arraying forms in 915 MHz and 2.45 GHz are shown in Table2. Final parameters of the proposed four-element arrays without additional ground in 2.45 GHz are optimized as follows: l = 60 mm, d = 85.6 mm, d
e = 67.3 mm, l
e = 7.2 mm, w = 90 mm, l
1 = 153.6 mm, w
1 = 24 mm, w
2 = 7 mm, w
3 = 2.5 mm, w
4 = 4 mm, w
5 = 0.8 mm, w
6 = 1 mm, w
7 = 3 mm, w
8 = 2 mm, w
9 = 0.8 mm, w
10 = 0.8 mm, w
11 = 0.7 mm, w
12 = 3.5 mm, l
2 = 21.2 mm, l
3 = 23.1 mm, l
4 = 4.6 mm, l
5 = 21.9 mm, l
6 = 4 mm, l
7 = 30.3 mm, l
8 = 30.5 mm, l
9 = 31.1 mm, l
10 = 22.5 mm, l
11 = 6 mm, l
12 = 5 mm,  and l
13 = 0.3 mm.Table 2
Values of main parameters.
Resonant frequency
Arraying form
d
e
(mm)
d (mm)
l (mm)
915 MHz
Two-element (no ground)
173.5
200.4
—
2.45 GHz
Four-element  (no ground)
67.3
85.6
60
2.45 GHz
Four-element (with ground)
57.1
79.2
60Fabricated antenna with additional ground is shown in Figure7. The bottom layer of antenna is 15 mm above additional ground. Simulated and measured return loss results are shown in Figure 8. Figure 8(a) presents simulated return loss without additional ground. The −10 dB band is from 2.32 GHz to 2.55 GHz. After installing additional ground, return loss decreases to −19 dB and the bandwidth reduces to 110 MHz as shown in Figure 8(b). Measured result basically tallies with simulated result, and the bandwidth meets the requirements of RFID 2.45 GHz (2.400 GHz–2.483 GHz). The radiation patterns in E-plane and H-plane are shown in Figure 9. The main lobe of E-plane radiates in vertical direction, verifying the method discussed before. Simulated and measured gains are shown in Figure 10. After installing additional ground, gain approximately increases by 3 dBi. Simulated gain of four elements without additional ground at 2.45 GHz bandwidth ranges from 6.6 dBi to 7 dBi. With additional ground, simulated gain increases to 9.9 dBi. Measured gain without additional ground is from 5.9 dBi to 7.5 dBi and with additional ground is from 9.1 dBi to 10.5 dBi within bandwidth. The simulated and measured gains are approximately the same and meet the requirements of RFID 2.45 GHz high-gain base station antenna.Figure 7
Fabricated antenna with additional ground.Simulated and measured return loss. (a) Without additional ground and (b) with additional ground.
(a)
(b)Simulated and measured radiation pattern. (a) E-plane and (b) H-plane.
(a)
(b)Figure 10
Simulated and measured gain.


## 5. Conclusion

This paper presents a design method of high-gain planar dipole-array antenna for 2.45 GHz. Gain is enhanced due to the same direction of current by reversing phase of two adjacent ports. By setting phase retardation of each array, radiation direction is controllable. Expressions of two and four elements are given and radiation pattern is calculated by MATLAB. Simulated return loss at resonant point is −35.3 dB with gain up to 7 dBi. Simulated gain with additional ground is up to 9.9 dBi. The maximum measured gain without additional ground is 7.5 dBi and with additional ground is 10.5 dBi. In general, the proposed planar dipole-array antenna is suitable for 2.45 GHz high-gain base station antenna with characteristics of high gain, controllable direction, and planarity.



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*Source: 704974-2014-01-30.xml*