# Experimental Target Tracking Using Asynchronous Sensors

Authors: Zhihua Lu; Mengyao Zhu; Qingwei Ye; Yu Zhou; Lingfu Xie
Journal: Wireless Communications and Mobile Computing
 (2018)

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## Abstract

We investigate the problem of target tracking using a wireless sensor network with asynchronous sensors. To study the impact of sensor clock imperfection on target tracking in practical situations, we build a testbed and collect data from an outdoor experiment. After analyzing the collected data, we find that the TDOA (time-difference-of-arrival) and FDOA (frequency-difference-of-arrival) measurements have notable bias, which is caused by asynchronous sensors or more precisely by the sensor clock drift. Based on the model of clock drift, the measurement bias and the target position are integrated into a state-space model. Both can be estimated in the framework of the extend Kalman filter. In some circumstance, the target trajectory is tracked successfully.


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## Body

## 1. Introduction

As an emerging wireless service and application, target positioning or tracking using the measurements collected in wireless sensor networks (WSNs) has drawn a lot of attention over the past two decades [1, 2]. Recent research interests lie in dealing with the practical environments, e.g., NLOS (non-line-of-sight) environment [3], multipath environment [4], and uncertain sensor positions [5].In this paper, we consider the practical case that the involved sensors are not perfectly synchronized. The asynchronism between sensors is caused by the local oscillator drift of sensors. In recent years, the problem of target positioning is investigated jointly with the problem of clock synchronization. In [6–8], a network composed of an unknown node and some synchronized anchor nodes is considered. In order to jointly estimate the unknown node’s location and clock parameters, the maximum likelihood (ML) estimator and a low-complexity least squares (LS) based estimator are derived in [6], two iterative approaches based on the Expectation-Maximization (EM) and the LS, respectively, are proposed in [7], and two suboptimal estimators based on semidefinite programming and linear estimation, respectively, are proposed in [8]. In [9, 10], by contrast, a fully asynchronous network is considered. A scheme of joint clock synchronization and ranging for all the nodes is proposed. More precisely, the solution based on the LS is given to jointly estimate all the unknown clock-skews, clock-offsets, and pairwise distances of the sensors.Instead of implementing distinct protocols (e.g., two-way message exchange) as the aforementioned work, the work in [11, 12] involves the information provided by the trajectory of a moving node and the periodicity of the transmitted signal to estimate the node’s location and clock information. In [13], a new technique for estimating fine clock errors and range between two nodes simultaneously based on round trip time measurements is proposed and tested based on the experimental data. The data is collected from an in-house testbed based on the impulse-radio ultrawideband (IR-UWB) technology. Generally speaking, very few estimation algorithms for clock parameter and location have been verified experimentally in the literature. This is mainly due to the lack of experimental testbeds or platforms.In this paper, we attempt to build an outdoor testbed using radio frequency, which can be used as a platform to test and validate different schemes of joint clock synchronization and localization of the nodes in WSNs. In addition, a simple scheme based on the extended Kalman filter (EKF) is proposed to track the target node’s location and clock parameters, which can deal with the case with nonstationary clock parameters. Recall that most of the existing methods are based on the stationarity assumption on the clock parameters.The remainder of the paper is organized as follows. The experimental setup is presented in Section2 and the collected data is analyzed in Section 3. In Section 4, the algorithm is described in detail. After that, we present the tracking result after implementing the proposed algorithm on the real data in Section 5. Finally, Section 6 concludes the paper briefly.


## 2. Experimental Setup

In the outdoor experiment, we use three sensors which are placed at different positions to track the trajectory of a moving target. The target to be tracked is a satellite phone. Someone is sitting in a moving car and making call using the satellite phone. The uplink signal of the phone can be sensed by our sensors, from which we can extract necessary information for tracking purpose, e.g., TDOA and FDOA measurements. The relative positions of sensors and the target trajectory are marked on a Cartesian coordinate plane; see Figure8 in Section 5.At the target side, there are mainly three items. First, the involved satellite phone product is Inmarsat IsatPhone pro. Second, an external magnetic mount antenna (i.e., Serial No. AT1595-90) is mounted on the top the car, in order to let the phone calling in the car. Third, a Trimble 5700 GPS Receiver is used to record the instantaneous position of the car, which is considered as ground truth in algorithm implementation.The sensor is built based on the USRP (Universal Software Radio Peripheral) (https://www.ettus.com) and related peripherals. All the components of the sensor are given in Figure1. The sensor contains an Antcom Iridium/Inmarsat/GPS antenna (i.e., Serial No. 0.5R1216P-XSM-4-GN-3in), a Mini-Circuits low noise amplifier (i.e., Serial No. ZHL-1217MLN), and its related DC power supply (i.e., Serial No. ELC-ALR3003), an Ettus USRP N210 with WBX daughterboard and a laptop as well as some necessary cables. Also, a LEAD-ACID 12V/65Ah battery and a related Pure Sine Wave power inverter are used to provide power for all the components of the sensor. The uplink signal of the satellite phone is received by Antcom Iridium/Inmarsat/GPS Antenna, amplified by Mini-Circuits low noise amplifier, processed by USRP’s daughterboard and mainboard, and finally stored in the laptop. Figure 2 shows the sensor prototype.Figure 1
Sensor components.Figure 2
Sensor prototype.We use the GPS-unlocked oscillators (or free-running local clocks) to synchronize the USRP. In this case, the USRPs’ local clocks are initialized roughly through the NTP service before recording the data. The NTP service needs WIFI access which is provided by a mobile phone. The free-running local clocks of the USRPs cause the bias of the TDOA and FDOA measurements, which is analyzed in the next section.


## 3. Measurement Bias Analysis

The uplink signal of the Inmarsat IsatPhone Pro is modulated by GMSK with a channel bandwidth of50 KHz and appears in the frequency range of 1642.50±17.5 MHz. In our recorded data, the center frequency of the uplink signal is located on 1644.225 MHz or 1644.275 MHz. The USRP has a center frequency of 1644 MHz and sampling rate of 10 MHz, which covers the potential frequency of the uplink signal in the experiment. A bandpass filter is used to filter out the uplink signal from the recorded signal by the USRP. We record the signal for 90 s. As an example, the uplink signal amplitude in the time period 80-80.1 s is given in Figure 3.Figure 3
The amplitude of the uplink signal in the time period 80s-80.1s.The initial synchronization between sensor clocks via NTP service is not very precise and can lead to the clock difference as large as 1 s. Since we have no prior knowledge of sensor clock parameters, we do manual calibration to achieve the clock difference smaller than 1 ms by inspecting received signal packet pattern. Based on the calibrated signals of three sensors, we use the generalized cross correlation algorithm [14] to estimate TDOA and FDOA values for each pair of sensors. For a couple of sensors, we estimate the TDOA and FDOA values every 10 ms so that the TDOA and FDOA measurements are updated every 10 ms. The true TDOA values are calculated based on the true positions of sensors and target. The target positions are recorded by the Trimble 5700 GPS Receiver mounted on the car that has a sampling rate of 10 Hz. Note that the altitude difference between sensors and target is ignored since it has limited impact on tracking accuracy compared to other error sources in the experiment scene.The local oscillator drift or simply the clock drift leads to significant bias when estimating TDOA and FDOA measurements. The biases of estimated TDOA values compared to the true ones are given in Figures4–6. (In the figures, the TDOA values are multiplied by the light speed.) Blue circles are the biases, that is, the estimated TDOA values minus the true ones. Black line is outcome of robust line fitting of blue circles. Red lines mark confidence interval of 3σ (σ=100 m) for black line. It means that all the blue circles outside the region between two red lines could be treated as outliers in the tracking algorithm.Figure 4
Bias of the estimated TDOA values for Sensor 1 and Sensor 2.Figure 5
Bias of the estimated TDOA values for Sensor 1 and Sensor 3.Figure 6
Bias of the estimated TDOA values for Sensor 2 and Sensor 3.The bias is suspected to be caused by two sources. One is imperfect synchronization between sensors, which can be roughly modeled by line fitting. If there is prior knowledge of the clock drift, e.g., obtained by training data or other sources, the modeling will be more accurate. However, it is not the case in our experiment. The other is propagation error in the channel between the target and sensors, e.g., multipath effect or non-line-of-sight (NLOS) error, which is hard to be modeled. In this paper, we focus on the bias caused by asynchronous clocks. In order to isolate the propagation error and model the synchronization error, only the data, which is suspected to be transmitted via the channel of good quality, is used for line fitting. More precisely, the data between 28 s and 90 s is used for line fitting in Figures4–6. Because the correlation value in this period is relatively high [14].The line fitting of the TDOA bias captures the trend of bias variation with respect to the time. This validates the linear model for TDOA bias caused by the clock drift, which will be presented in the next section. It is worth mentioning that the measurement bias is modeled roughly by the line fitting in this section and will be estimated more accurately in the next section. The result of line fitting is used for the initialization for the estimation procedure.The estimated FDOA values has relatively small bias and large variance, compared to the TDOA values. The FDOA bias also can be modeled by line fitting. However, the FDOA measurement is not informative as the TDOA measurement in our case. We do not attempt to present the result of the estimated FDOA values here.


## 4. Algorithm Description

To implement tracking algorithm, the measurement bias must be estimated simultaneously with the target position. Therefore, we have to study the mechanism of clock drift producing the measurement bias.The local timeti of Sensor i with respect to a universal standard time t is defined as(1)ti=βit+αiwhere βi and αi are clock skew and clock offset, respectively. In order to describe the clock error of sensors, we use the well-known two-state clock model in [15]:(2)αk,iβk,i=1T001αk-1,iβk-1,i+nk-1,i where k is the time step, T0 is the duration of a time step, and nk-1,i is a Gaussian noise vector with zero mean and covariance matrix of(3)Qc=σ12T0+σ22T033+σ32T0520σ22T022+σ32T048σ22T022+σ32T048σ22T0+σ32T033with typical values σ12=5.25×10-24 and σ22=1.77×10-21 for the oven-controlled crystal oscillators of the USRP in our test bed [16]. In what follows, we describe the impact of the clock parameter on the TDOA and FDOA measurements.For a pair of sensors, e.g., Sensori and Sensor j, the TDOA and FDOA values are defined by(4)TDOAk,ij=1csi-sk-sj-skFDOAk,ij=-f0cvi-vkTuk,i-vj-vkTuk,jwhere c denotes the light speed, f0 denotes the carrier frequency of the target signal, and k is the time step. Herein, sk and vk are the location and velocity of the target at time step k, whereas si and vi are the location and velocity of Sensor i. Note hat si is known and vi is [0,0]T m/s since the sensors are fixed at predetermined locations. The unit position vector uk,i from the target position at time step k to Sensor i is given by(5)uk,i=si-sksi-sk.Since each pair of sensors produces a set of TDOA and FDOA values, we will haveM=N(N-1)/2 sets of TDOA and FDOA values given N sensors. For simplicity, define τk,ij and ξk,ij as TDOA in distance and FDOA in velocity between Sensors i and j at time step k:(6)τk,ij=c·TDOAk,ijξk,ij=-cf0·FDOAk,ij. Due to the relative clock drift between sensors, the estimated TDOA and FDOA values, e.g., τ^k,ij and ξ^k,ij, based on the received signals by sensors can be formulated approximately as follows [17]:(7)τ^k,ij≈τk,ij+θk,ij+ωk,1ξ^k,ij≈ξk,ij+ϕk,ij+ωk,2where ωk,1 and ωk,2 are the measurement noise, which are assumed to be Gaussian distributed with zero means. Herein, θk,ij and ϕk,ij are the bias contributed by the clock drift between two sensors. Moreover, θk,ij and ϕk,ij also can be captured by the two-state state-space model as in (2)(8)θk,ijϕk,ij=1T001θk-1,ijϕk-1,ij+υk-1,ijwhere υk-1,ij is the zero mean Gaussian noise but with a different covariance matrix compared to Qc in (3). However, the difference is not significant so that Qc in (3) is used for the covariance matrix of υk-1,ij. As mentioned before, the TDOA bias is much larger than the FDOA bias, i.e., θk,ij≫ϕk,ij.We stack only the Sensor 1 related TDOA and FDOA bias in order into two column vectors:(9)bk,1=θk,12,…,θk,1NTbk,2=ϕk,12,…,ϕk,1NT.Define bk=[bk,1T,bk,2T]T and(10)Π=1T001,and it follows from (8) that(11)bk=Π⊗IN-1bk-1+vk-1where ⊗ denotes the Kronecker product, IN-1 denotes identity matrix of size N-1, and the noise vk-1 is Gaussian distributed with zero mean and covariance matrix of(12)Qb=Qc⊗IN-1where Qc is given in (3).Now, we can stack the TDOA and FDOA measurements at time step k in order into two column vectors, i.e.,yk,1 and yk,2, respectively. Then, as mentioned before, the TDOA bias is much larger than the FDOA bias, yk,1 is a M dimensional vector with the elements τ^k,ij,i=1,…,N-1,j=i+1,…,N, whereas yk,2 is also a M dimensional vector with the elements ξ^k,ij,i=1,…,N-1,j=i+1,…,N. In our experiment, N=3 and M=3. We obtain(13)yk,1=τ^k,12,τ^k,13,τ^k,23Tyk,2=ξ^k,12,ξ^k,13,ξ^k,23T.Letτk and ξk be the column vectors stacking all τk,ij’s and ξk,ij’s at time step k. Then, following (7) we obtain(14)yk,1=τk+Abk,1+ωk,1yk,2=ξk+Abk,2+ωk,2where ωk,1 and ωk,2 are stacked noise. bk,1 and bk,2 are given in. (9). A is the transition matrix which transits a N-1 dimensional column vector into a M dimensional column vector. It shows the relationship between the measurement biases of all the sensor pairs. For example, when N=3, it can be readily derived that (15)A=1001-11.The target state includes the position and velocity; that is,(16)xk=skT,vkTT.Then, the state-space model for the target is given by(17a)xk=Fxk-1+Guk-1(17b)bk=Π⊗IN-1bk-1+vk-1(17c)yk,1=h1xk+Abk,1+ωk,1(17d)yk,2=h2xk+Abk,2+ωk,2where(18)F=I2T0·I202I2,G=T022·I2T0·I2,and uk-1 is a 2-dimensional Gaussian vector with zero mean and covariance matrix of Qx. Following from (4), (6), and (14), we derive the M dimensional vectors h1xk and h2xk, respectively, with elements(19)h1,ij=si-sk-sj-skh2,ij=vi-vkTuk,i-vj-vkTuk,jwith i=1,…,N-1,j=i+1,…,N. ωk,1 and ωk,2 are both Gaussian distributed with zero means and covariance matrices of R1 and R2, respectively.If we definezk=[xkT,bkT]T, yk=[yk,1T,yk,2T]T, ωk=[ωk,1T,ωk,2T]T, as well as(20)F~=F04×2N-102N-1×4Π⊗IN-1and(21)νk-1=Guk-1vk-1,we rewrite (17a), (17b), (17c), and (17d) as(22a)zk=F~zk-1+νk-1(22b)yk=h~zk+ωkwhere(23)h~zk=h1xk+Abk,1h2xk+Abk,2.νk-1 and ωk are Gaussian distributed with zero means and covariance matrices of(24)Q~=GQxGT04×2N-102N-1×4Qband(25)R~=R10M0MR2,respectively.The extended Kalman filter for the state-space model in (22a) and (22b) can be given by(26)z^k-=F~z^k-1Pk-=F~Pk-1F~T+Q~Sk=H~kPk-H~kT+RKk=Pk-H~kTSk-1z^k=z^k-+Kkyk-h~z^k-Pk=I-KkH~kPk-where(27)H~k=Hk,110M×2A0M×N-1Hk,21Hk,220M×N-1A.Herein, Hk,11, Hk,21, and Hk,22 are the matrices of size M×2 with their rows(28)Hk,11,ij=-uk,i+uk,jTHk,21,ij=-I-uk,iuk,iTvi-vksi-sk+I-uk,juk,jTvj-vksj-skTHk,22,ij=-uk,i+uk,jTwhere i=1,…,N-1,j=i+1,…,N.As a summary, the EKF in (26) can estimate the measurement bias and the target position simultaneously. It is worth mentioning that the 3σ rejection is adopted to reject suspicious outliers of the TDOA and FDOA measurements in EKF formulation in (26). It means that all the blue circles outside the region between two red lines in Figures 4–6 are discarded in the EKF computation.


## 5. Tracking Results

Before implementing the EKF, some initial values should be set appropriately. By inspecting the TDOA and FDOA measurements, we can setR1=104I6 and R2=302I6 for the measurement model. We set the time interval T0=0.01 s and Qx=0.1I2 for the dynamic model. The initial velocity of target is set as 0 m/s. The initial position is set as the true position.The initial measurement biasb0 in (9) is supposed to be set according to the prior knowledge about the clock parameters. In our case, we do not have such information so that we have to extract it from the TDOA and FDOA measurements. b0 is set according to the outcome of line fitting of the TDOA and FDOA measurements in Section 3. However, the above initial bias value could be far from the true one. To compensate this, we have to set the bias variance much larger than its theoretical value, i.e., σ12=10-20, σ22=10-18, and σ32=10-16. The tracking of the true measurement bias resorts to the EKF. Note that we do not have the ground truth of the clock drift so that it is impossible to check the performance of measurement bias estimation directly. Instead, we can check the trajectory tracking result.Figures7 and 8 demonstrate the sensor positions, the true target trajectory, and the estimated trajectory. In Figure 7, the full set of data is used, whereas in Figure 8, a partial set of data, i.e., from 40 s to 90 s, is used. It is seen that the tracking error between 0 s and 40 s is much larger than between 40 s and 90 s. The performance difference is caused by the quality of the TDOA and FDOA measurements. In Figures 4–6, we can find that the TDOA values estimated from the data between 0 s and 40 s are sparser than that between 40 s and 90 s. It indicates that the channel quality of the former is lower than that of the latter. The low channel quality leads to the low measurement quality, which directly impacts the tracking accuracy. A large amount of error is accumulated in the former period so that the tracking cannot converge well even when the data is of good quality later on.Figure 7
Estimated trajectory using data from 0 s to 90 s.Figure 8
Estimated trajectory using data from 40 s to 90 s.According to the EKF formulation in Section4, the bias and trajectory are estimated together. The inaccurate bias initial setting definitely influences the trajectory estimation. In Figure 8, it is seen that there is a notable tracking error around the time 50 s. This error is supposed to be caused by the inaccurate initial setting for the bias. After the EKF filtering over sufficiently large amount of samples, the measurement bias can be estimated correctly, which improves the accuracy of the trajectory tracking. The Root Mean Square Error (RMSE) of the estimated positions in Figure 8 is about 18 meter.It can been seen that the estimated trajectory deviates from the true one at the end of target motion (i.e., around 90 s). It is supposed to be caused by model mismatch of the TDOA and FDOA measurement noise. Recall the measurement noise is assumed to be Gaussian distributed with zero mean; seeωk,1 and ωk,2 in (7). However, for some collected data, the measurement noise does not exactly follow the assumed Gaussian distribution, which can be observed in Figure 4, for example. In Figure 4, the TDOA biases (blue circles) located in the interval between 85 s and 90 s are not distributed symmetrically around the center (black line).


## 6. Conclusion

We build an outdoor testbed in order to jointly track target location and clock parameter. The main challenge of target tracking in our experiment is the nonnegligible measurement bias caused by the sensor clock drift. The collected TDOA and FDOA measurements validates the theoretical state-space model of clock parameters. Following this, the measurement bias can be modeled. The EKF is used to track the measurement bias (or clock parameters) and the target trajectory simultaneously. The tracking result directly depends on the channel quality. When the channel is of good quality, the target trajectory is successfully tracked. The channel effect on the measurements, including multipath and NLOS propagation, is not well studied in this paper. This should be investigated in the future work. Besides, using the developed testbed to validate the existing algorithms is expected to be investigated in the future.



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*Source: 7059048-2018-10-08.xml*