# Ultrasmall Dual-Band Metamaterial Antennas Based on Asymmetrical Hybrid Resonators

Authors: Ji-Xu Zhu; Peng Bai; Jia-Fu Wang
Journal: International Journal of Antennas and Propagation
 (2016)

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## Abstract

A new type of hybrid resonant circuit model is investigated theoretically and experimentally. The resonant model consists of a right hand (RH) patch part and a composite right and left handed (CRLH) part (RH + CRLH), which determines a compact size and also a convenient frequency modulation characteristic for the proposed antennas. For experimental demonstration, two antennas are fabricated. The former dual-band antenna operating atf-1=3.5 GHz (Wimax) and f+1=5.25 GHz (WLAN) occupies an area of 0.21λ0×0.08λ0, and two dipolar radiation patterns are obtained with comparable gains of about 6.1 and 6.2 dB, respectively. The latter antenna advances in many aspects such as an ultrasmall size of only 0.16λ0×0.08λ0, versatile radiation patterns with a monopolar pattern at f0=2.4 GHz (Bluetooth), and a dipole one at f+1=3.5 GHz (Wimax) and also comparable antenna gains. Circuit parameters are extracted and researched. Excellent performances of the antennas based on hybrid resonators predict promising applications in multifunction wireless communication systems.


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## Body

## 1. Introduction

Over the past decade, artificial electromagnetic (EM) metamaterials (MTMs) have intrigued long-hold interests due to their abundant abnormal behaviors that are not occurring in nature. As a result, scientists and engineers have endeavored theoretically and experimentally to bring these special MTMs into applications such as microwave devices [1] and new functional devices [2]. As an important part for wireless communication system, antennas based on MTMs have developed rapidly with enhanced performances such as high directivity, multibeams, multifrequency, and broad bandwidth [3–7].Resonant antennas by loading MTMs are interesting for researchers for their compact size and multibands characteristic, among which two categories are most important. Firstly, resonant antennas using composite right and left handed (CRLH) transmission line (TL) are in advantage of compact structure, while they suffer from an easy method of frequency modulation [8, 9]. For another, hybrid resonant multifrequency antennas with a symmetrical structure of right handed patch, CRLH part, and right handed patch (RH + CRLH + RH) are capable of frequency modulation [10–16], while they are not sufficient in miniaturization.To solve the above issues, in this paper, a new kind of CRLH TLs has been proposed by loading complementary spiral resonators (CSRs) in the conventional mushroom structure. And a novel asymmetrical hybrid resonant circuit model is investigated theoretically for the first time in Section2. For verification and experimental applications, two dual-band dual-mode antennas are designed, fabricated, and measured. In Section 3, a patch antenna filled with 1 × 2 conventional mushroom structures is investigated. In Section 4, dual-band ultrasmall antenna by loading CSRs for further miniaturization and easy frequency modulation is studied. Circuit parameters are extracted for deep insight into the working mechanism of the hybrid resonant circuit model. Finally, a conclusion of the whole paper is made.


## 2. CRLH Cell Design and the Working Mechanism of Novel Asymmetrical Hybrid Resonator

To date, various types of CRLH TLs have been investigated since the first proposal. Metallic via holes, as the most important structure to provide LH inductor, have been applied to design CRLH TLs, especially for the mushroom CRLH TL (short for mushroom). In order to design an electrically smaller MTM and make a progress toward homogenized medium [17], a combination of two turns CSRs and mushroom structure is considered and optimized. For comparison, the conventional mushroom cell and the CSRs-loaded mushroom cell are shown in Figure 1.Figure 1
Topology of the conventional mushroom and CSRs-loaded mushroom structures. Perspective of (a) conventional mushroom cell and (b) CSRs-loaded mushroom element; (c) top and bottom view of the CSRs-loaded mushroom unit as well as geometrical dimensions.
(a) (b) (c)For design and analysis, the proposed mushroom TL cell and the upcoming antenna design are investigated on the F4B substrate with a dielectric constant ofδ=2.65 and a thickness of h=3 mm. The finite element method (FEM) based commercial software Ansoft HFSS is employed for full-wave EM simulation and Ansoft Serenade for electrical simulation. To gain a better understanding of the principle of the proposed CRLH TL, the dispersion curve is calculated and simulated using HFSS. Figure 2(a) compares the simulated dispersion diagram of the conventional mushroom and the CSRs-loaded mushroom structures. It is worth noting that the LH characteristic is clearly observed in the region of 5.51–7.25 GHz for the conventional mushroom structure, whereas it dramatically shifts downward to 2.15–3.30 GHz for the CSRs-loaded mushroom element. The reflection coefficients are also simulated for a complementary research with the results shown in Figure 2(b). It is obvious that the resonant frequency is about 6.5 GHz for the conventional mushroom cell and 2.2 GHz for the CSRs-loaded one, which further demonstrated the miniaturization by loading the CSRs perturbation. The increased LH inductor by etching the CSRs in the ground plane gives rise to a resonant frequency reduction of 66.15%. And it may be an effective method to design electronic smaller antenna by loading the CSRs structure.Figure 2
Dispersion diagram and simulatedS-parameters of the conventional mushroom and CSRs-loaded mushroom TL structures.
(a) (b)For a symmetrical RH + CRLH + RH resonator, two RH patches are essential for frequency manipulation [10–16]. However, for an electrically small CRLH resonator, frequency modulation is not convenient [8, 9]. So a novel asymmetrical hybrid resonator consisting of RH + CRLH is concerned and investigated. The equivalent circuit model is shown in Figure 3. As expected, the final circuit model is actually a combination of RH patch part and CRLH part; for convenience and not losing universality, two CRLH cells are chosen. Completely different from conventional hybrid resonator, only one RH part is reserved aiming at both miniaturization and frequency manipulation. In the circuit model, the letter C represents the coupling between the RH part and CRLH section. The EM response of the RH patch is modeled by the parallel resonant tank formed by CR and LR, and R represents the radiation resistance. For the CRLH parts, the left handed (LH) capacitor Cg is provided by the slot coupling between adjacent cells. LH inductor Lp is acquired by the metallic via hole connected to the ground, and Lp1 is added for the frequency response of CSRs inserted in the mushroom structure. Ls and Cp is the inherent inductance and capacitance. C1 accounts for the fringing capacitance of the gap. R1 is set very large to simulate the condition of open circuit.Figure 3
Illustration of the hybrid resonant equivalent circuit model.According to the circuit model in Figure3, the dispersion relation for the novel resonant circuit model is as follows:(1)βnL=βnRHd+βnCRLHpN,where the length of RH patch is defined as d and βnRH is phase constant of the RH patch and can be calculated as:(2)βnRH=wLRCR.The number and propagation constant of the CRLH TL cells are defined asN and βnCRLH decided as(3)βnCRLHp=cos-1⁡1-0.5wL2w2+w2wR2-wL2wse2-wL2wsh2,where wL, wR, wse, and wsh can be calculated as(4a)wL=1CgLp+Lp1,(4b)wR=1CpLs,(4c)wse=1CgLs,(4d)wsh=1Cp+C1Lp+Lp1.Then the resonant modes n can be obtained by the following condition:(5)βnL=nπn=-N+1,-N+2,…,0,1,2,…,N-2,N-1.According to (1)–(5), two aspects should be highlighted. First, the resonant frequency is determined by both the RH patch and CRLH sections as the conventional hybrid resonator. Then, size reduction is available for a missing of RH patch and frequency modulation characteristic does not deteriorate with a combination of RH part and CRLH section.


## 3. Dual-Band Antenna Design Using Hybrid Resonant Circuit Model

According to the principle of the proposed hybrid resonator, a compact dual-band antenna shown in Figure4 operating at f-1=3.5 GHz (Wimax band) in n=-1 mode and f+1=5.25 GHz (WLAN band) in n=+1 mode is designed by optimizing the RH patch and mushroom cells cautiously. As shown in Figure 4, the novel antenna consists of a metal patch and 1 × 2 conventional mushroom cells. The whole dimension of the antenna is just 17.8 mm × 10 mm, evaluated as 0.21λ0×0.08λ0. It is promising that the proposed antenna is 90.31% smaller than conventional half wavelength antenna operating at 3.5 GHz, indicating a desirable performance in recent higher integration circuit.Figure 4
Perspective view of the proposed dual-band antenna with geometrical parameters (in mm).Impedance match is essential to the radiation efficiency of an antenna, especially for dual-band or multiband antenna which is difficult to be good impedance matches at all operation bands. Here three conditions are adopted to achieve a good antenna performance. Feeding without slot, with one-annular-ring slot corresponding to a capacitance, and with a two-annular-ring slot equal to a shunt capacitance is used to compensate the feeding port, respectively. The input impedance for three conditions is simulated and depicted in Figure5(a). Obviously, the curve for the antenna feeding with a two-annular-ring slot has the flattest curves compared to that of the other two cases at both bands, indicating an improved impedance matching. For further analysis, the reflection coefficients under the three cases are shown in Figure 5(b). It is clearly observed that the antennas feeding with one-annular-ring slot or without slot shows poor impedance matches, especially for the one feeding without slot, while the return loss is less than −14.5 dB for both bands of the antenna feeding with two-annular-ring slot (see Figure 6).Figure 5
Simulated electric field distributions and 3D radiation patterns. Electric field distribution at (a) 3.5 GHz and (b) 5.25 GHz. 3D radiation patterns at (c) 3.5 GHz and (d) 5.25 GHz.
(a) (b) (c) (d)Figure 6
Simulated (a) input impedance and (b)S-parameters feeding with no slot, one-annular-ring slot, and two-annular-ring slot, respectively.
(a) (b)Figure5 illustrates the simulated electric field distributions and 3D radiation patterns for two interesting modes, respectively. It is observed that the electric fields are 180° out of phase corresponding to a half wavelength at f-1=3.5 GHz and f+1=5.25 GHz, respectively. The discrepancy of electric field distribution in the mushroom structures gives rise to different kinds of radiation modes, indicating that the antenna operates with a combination of RH patch and mushroom parts. As a consequence of similar 180° out-of-phase electric field distribution, patch-like radiation patterns are expected in Figures 5(c) and 5(d).For experimental verification, the proposed antenna has been fabricated, assembled, and measured with return loss through a ME7808A vector network analyzer while radiation patterns are through the far-field measurement system in an anechoic chamber. Figure7 depicts the return loss of the proposed antenna with the photograph displayed in the inset. Obviously, the return loss for the EM simulation and circuit simulation and measurement are in good agreement, indicating the rationality and accuracy of the asymmetrical hybrid resonant circuit model. As the measured result shows, the −10 dB impedance bandwidths for both bands are 51 MHz and 32 MHz with the center frequencies located at 3.5 GHz and 5.25 GHz, respectively. The bandwidth of the proposed antenna is determined by the Q value of the resonators, which can be enhanced by increasing the antenna size or substrate thickness. The simulated and measured radiation patterns in the two principal planes are shown in Figure 8. As expected, the experimental results are in excellent consistency with the simulated ones with patch-like patterns at both bands. And the measured antenna gain reaches 6.2 and 6.1 dB, respectively. At 3.5 GHz, the peak of the cross-polarization is −10.8 dB in the E-plane and −12.6 dB in the H-plane. And, at 5.25 GHz, the values of the cross-polarization are both lower than −10.3 dB around the radiation direction.Figure 7
Simulated and measured return loss for the dual-band antenna with the photograph displayed in the inset. The shadow represents the −10 dB bandwidth of the proposed antenna.Figure 8
Radiation patterns of the proposed dual-band antenna. (a) E-plane at 3.5 GHz; (b) H-plane at 3.5 GHz; (c) E-plane at 5.25 GHz; (d) H-plane at 5.25 GHz.
(a) (b) (c) (d)


## 4. Ultrasmall Antenna Design Using Hybrid Resonator

For further verification and comprehensive analysis of the proposed resonant circuit model, another ultrasmall dual-band antenna operating atf0=2.4 GHz (Bluetooth band with the mode n=0) and f+1=3.5 GHz (Wimax band with the mode n=+1) is designed with the typology shown in Figure 9. We have demonstrated that CSRs are of importance to increase of LH inductance, resulting in an electrical smaller structure and easier method for frequency manipulation. Here CSRs are introduced in the asymmetrical patch antenna with detailed geometrical parameters in Figure 9. The final size of the patch is just 19.8 × 10 mm2, corresponding to 0.158λ0×0.08λ0, which is smaller than 127% compared with the available MTM antennas based on mushroom structures [9, 16]. Also a two-semiannular-ring slot is used for good impedance matches at both bands.Figure 9
Schematics of the proposed antenna with geometrical parameters (in mm).Figure10 plots the curve of S11 for EM simulation, circuit simulation, and measurement. A desirable agreement between the EM simulated and circuit simulated results verifies the rationality of the proposed asymmetrical hybrid resonant circuit model for a second time. Meanwhile a slight frequency blueshift is obtained for the measured result which can be ascribed to the inherent tolerance in the fabrication process. From the measured result, two operating bands show 10 dB impedance bandwidths of 25 MHz around f0 and 50 MHz near f+1, corresponding to 1.04% and 1.43%, respectively.Figure 10
Simulated and measured return loss with the photograph of antenna displayed in the inset. The shadow represents the −10 dB bandwidth of the proposed antenna.To extensively analyze the working mechanism of different working modes, the electric field distribution at the patch radiator is shown in Figure11. Referring to Figure 11(a), the electric field is in phase along the xoy plane in the mode n=0 at f0=2.4 GHz, indicating that an infinite wavelength is supported at the ZOR frequency. As appreciated, the omnidirectional 3D radiation pattern is observed in Figure 11(c), when, at the mode n=+1, an out-of-phase electric field distribution is obtained along the x direction, indicating a patch-like radiation pattern at f+1=3.5 GHz shown in Figure 11(d).Figure 11
Simulated electric field distributions and 3D radiation patterns. Electric field distribution at (a) 2.4 GHz and (b) 3.5 GHz. 3D radiation patterns at (a) 2.4 GHz and (b) 3.5 GHz.
(a) (b) (c) (d)The radiation patterns at two special modes are measured in two principle planes with the results shown in Figure12. According to the radiation patterns, it is obvious that the experimental results are in excellent consistency with the simulated ones. A monopolar and a patch-like patterns are observed as expected in both modes n=0 and n=+1. A low cross-polarization less than −15.2 dB is observed except the one in the H-plane of n=0 mode. The cross-polarization level is about −7.5 dB lower than the copolarization at around −90° and 110°, which is due to the radiation of CSRs-loaded mushroom at the edge of the patch. In addition, the antenna exhibits a peak gain of 2.23 dB and 5.72 dB for both bands, respectively. The relative lower gain for n=0 is due to the omnidirectional radiation pattern in H-plane.Figure 12
Radiation patterns of the proposed antenna. (a) E-plane at 2.4 GHz; (b) H-plane at 2.4 GHz; (c) E-plane at 3.5 GHz; (d) H-plane at 3.5 GHz.
(a) (b) (c) (d)For a deep insight into the working mechanism of the hybrid resonant circuit, a detail comparison of circuit parameters and antenna performances are shown in Table1. Clearly, the LH inductor consisting of Lp and Lp1 increases 115.8% with the insertion of CSRs, resulting in lower working frequencies as well as a compact structure. The coupling between the mushroom and CSRs gives rise to the increasing of the parameter values of Ls and Cg. The value of radiation resistance R is larger for antenna II, indicating a higher antenna gain. A similar RH patch structure for the two antennas gives rise to almost the same parameter values of RH parts. A comparison of the antenna performances has been provided in Table 2. It can be seen clearly that the proposed antennas are electrically smaller compared with these references. Moreover, the measured antenna gain is very comparable with those references [10, 16].Table 1
Comparison of circuit parameters and performances for proposed two antennas.
Antenna type CRLH part Size C g (pF) L s  (nH) C 1 (pF) C p  (pF) L p  (nH) L p 1  (nH) I 0.42 2.24 0.16 1.95 1.01 0 0.21 λ 0 × 0.08 λ 0 II 0.49 4.3 0.15 1.92 0.98 1.2 0.158 λ 0 × 0.08 λ 0  Antenna type RH part WF (GHz) BW (MHz) Gain (dB) C (pF) C R (pF) L R (nH) R(Ω)  I 0.21 5.48 1.88 3.25 3.5/5.25 51/32 6.1/6.2 II 0.21 5.46 1.91 3.05 2.4/3.5 25/50 2.23/5.72Table 2
Comparison of antenna performances between the literature and this work.
References Antenna size (λ0) Operating frequency (GHz) Bandwidth (−10 dB) Measured gain (dB) [6] 0.2 × 0.2 × 0.017 3.5 3.77% 4.6 [10] 0.177 × 0.181 × 0.025 2.58 4.60% 2.98 [11] 0.17 × 0.33 × 0.019 3.52 — 4.5 [12] 0.246 × 0.246 × 0.03 1.5/2.4/3.5 2.63%/3.28%/6.44% 4.93/2.85/5.12 [13] 0.29 × 0.29 × 0.06 1.81/2.2 —/~2% 4.5/6.8 Pro.I 0.21 × 0.08 × 0.035 3.5/5.25 1.46%/0.61% 6.2/6.1 Pro.II 0.158 × 0.08 × 0.024 2.4/3.5 1.04%/1.43% 2.23/5.72



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*Source: 7019268-2016-11-20.xml*