# Sparse Representation Based Range-Doppler Processing for Integrated OFDM Radar-Communication Networks

Authors: Bo Kong; Yuhao Wang; Henry Leung; Xiaohua Deng; Huilin Zhou; Fuhui Zhou
Journal: International Journal of Antennas and Propagation
 (2017)

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## Abstract

In an integrated radar-communication network, multiuser access techniques with minimal performance degradation and without range-Doppler ambiguities are required, especially in a dense user environment. In this paper, a multiuser access scheme with random subcarrier allocation mechanism is proposed for orthogonal frequency division multiplexing (OFDM) based integrated radar-communication networks. The expression of modulation Symbol-Domain method combined with sparse representation (SR) for range-Doppler estimation is introduced and a parallel reconstruction algorithm is employed. The radar target detection performance is improved with less spectrum occupation. Additionally, a Doppler frequency detector is exploited to decrease the computational complexity. Numerical simulations show that the proposed method outperforms the traditional modulation Symbol-Domain method under ideal and realistic nonideal scenarios.


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## Body

## 1. Introduction

With the revolutionary development in wireless communication and radar technologies, spectrum resource is increasingly valuable. In order to alleviate the spectrum scarcity problem, research works have integrated radar into wireless communications [1–5]. Radar and communication functions can share hardware and software components, such as digital signal processing chips, RF module, and antenna. As a result, spectrum efficiency can be improved and the size of the integrated system can be decreased. However, most of these traditional systems were designed for single user, few of them consider multiuser scenarios, such as the device-to-device (D2D) communication [6], vehicle-to-vehicle (V2V) communication [7], and intelligent transportation system (ITS) [8]. Due to the congested channel environments and interuser interference, it is challenging to manage resources and guarantee the overall performance for both communication and radar systems, especially for dense multiuser applications.The concept of the integrated radar-communication system (RadCom) was first proposed in [9]. It was then further characterized by time domain [10–12] and code-domain integration in [13–17]. Although these techniques are common in wireless communications, they are not suitable for multiuser radar applications. With regard to the code-domain method, each user occupies the entire bandwidth, and it is difficult to separate different users without any performance degradation. Multiuser interference can lead to low dynamic range and affect the radar performance seriously [2]. In addition, multiuser access in the time domain via different time slots is not favorable since a radar system usually does not allow any additional delay, especially in safety applications. Besides, incoherent multiple measurements may produce range and Doppler ambiguity. Similarly, multiple access based on code division multiple access (CDMA) is not adaptable in radar applications. The reason is that CDMA can cause inherent interference and deteriorate the performance of radar [2, 18].Multiple access methods based on frequency domain, for example, the orthogonal frequency division multiplexing (OFDM) modulation, are attractive in radar and communication applications. A recent modulation Symbol-Domain method which takes full advantage of the OFDM time-frequency structure has been proposed in [19]. With the modulation Symbol-Domain method, the imperfect autocorrelation properties of the nonideal waveform are eliminated. Moreover, orthogonal frequency division multiplexing access (OFDMA) has been widely applied in modern mobile communication systems with certain groups of continuous subcarriers. However, this will deteriorate the range resolution for radar applications. To overcome this problem, a multiuser access method with uniformly interleaved subcarriers for OFDM radar network was proposed in [18]. However, ambiguity in range estimation is caused by periodic allocation of subcarriers, especially when the number of users is large. A detector with a variable threshold mask for random allocated subcarriers was proposed in [20]. However, the interferences caused by intrinsic signal property and multiuser access were not mitigated actually, which may result in a serious performance loss.Sparse representation (SR) is the basis of sparsity related information reconstruction methods, including compressive sensing, low-rank representation, and dictionary learning. SR-based algorithms can effectively recover information from randomly undersampled data [21–23]. With the advance of computing technology, SR-based methods have become feasible tools for various applications, such as synthesis and diagnosis of antenna arrays [24–26], radar sensing [27–29], and radar imaging [30–32]. With regard to the radar scenes, the number of targets is much smaller than the total number of grids to be solved. This can lead to an additional sparse constraint, which facilitates the utilization of SR theory.In this paper, a method that combines modulation Symbol-Domain and SR is proposed. Instead of allocating subcarriers uniformly, we propose a random subcarrier allocation mechanism for each node in the integrated radar-communication network and derive the corresponding signal processing algorithm based on SR method to estimate range and Doppler frequency shift simultaneously. From the perspective of SR, signals are random undersampled in the frequency domain which corresponds to the random allocated subcarriers. We consider the nonfluctuating moving point targets with the presence of additive white Gaussian noise (AWGN) and multiuser interferences.The contributions are as follows:(1)
A novel random subcarrier allocation mechanism with OFDM waveforms is proposed in order to improve the radar performance with less spectrum occupation in multiuser RadCom network applications.(2)
A range-Doppler estimation method is proposed based on the modulation Symbol-Domain and SR techniques. It is equivalent to an undersampled two-dimensional sinusoid wave estimation so that the partial discrete Fourier transform (DFT) matrix is employed as the dictionary.(3)
Simulation results are provided with different parameters for single user and multiuser scenarios. The proposed method is evaluated with multiuser interferences and provides an improved performance compared with classical methods. Furthermore, sensitive analysis of threshold factor is provided for the Doppler frequency detector, which corresponds to the computational efficiency in different scenarios.The rest of this paper is organized as follows. In Section2, we present the radar model and problem statement for the RadCom network. Section 3 describes the SR-based range-Doppler signal processing approach for the RadCom network with the proposed multiusers access mechanism. Simulation results for radar performance analysis and comparison with classical methods are presented in Section 4. Finally, concluding remarks are drawn in Section 5.


## 2. Radar Model and Problem Statement

In this paper, we consider a simplified model for RadCom network system with several cooperative RadCom nodes. Each RadCom node uses its omnidirectional antenna to transmit OFDM signals modulated by arbitrary information and receives reflected signals by a directional antenna. Meanwhile, signals transmitted by this node arrive at the receiving ends of other nodes for communication purposes. If two or more nodes transmit signals simultaneously, their signals are required to be differentiated by using a multiaccess technique.


### 2.1. RadCom Network Setup

Figure1 [19] shows a typical RadCom network. Those nodes are capable of maintaining communication links between themselves and maintaining active sensing of the target scene using the backscattered signals. The communication and radar functionalities occur simultaneously. The RadCom signal is used for both communications among RadCom nodes and target localization. Specifically, the RadCom signal is transmitted from the car on the left which establishes a communication link with the car on the upper right. At the same time, this RadCom signal is reflected by some objects, that is, the car on the middle right side. The car on the left receives the reflected signal and estimates the range and velocity of the target by using related signal processing methods. Simultaneously, signals from other RadCom nodes, that is, the car on the bottom right, are received by the car on the left and interfere with the receiver.Figure 1
RadCom network in ITS applications [19].A mechanism similar to general OFDMA is used for multiuser access. Each RadCom node needs to know the instantaneous channel occupancy information when they transmit signals. Instead of using periodical or grouped subcarriers, the idea in this paper is to choose a random set of subcarriers for each node. Nevertheless, the subcarriers allocated to each user are not specified by the user itself entirely but preassigned by the RadCom network protocol and selected by the user with appropriate broadcast protocols. The problem of channel overlap between users can be avoided in this way. In this paper, we focus on the related radar signal processing method. Issues like broadcast protocols can be solved by the existing wireless communication protocols [33].


### 2.2. RadCom Node Transmitter Subsystem

Figure2 presents the internal architecture of a single RadCom node. A channel allocation module corresponding to the subcarrier allocation protocol is introduced in order to provide subcarrier information for both transmitter and receiver of each user. When there are M users, each user is assigned with K randomly selected subcarriers according to a uniform distribution. Let Am denote the set of active subcarrier indices reserved for user m, so that ⋃m=1MAm={1,…,K} and Am∩Am′=⌀. As shown in [34], the random selection of the frequency samples guarantees that the DFT matrix obeys the restricted isometry property (RIP) with high probability, which is necessary for SR-based techniques. The module named Divide is related to the modulation Symbol-Domain method, which is used for eliminating the modulation information while performing radar sensing functions. More details are presented in Section 3.Figure 2
RadCom node architecture.Figure3 shows a case of random selected subcarrier allocation and its corresponding power spectrum of the transmitted signal. In this case, the number of subcarriers is 64, which is one-sixteenth of the number of total available subcarriers.Figure 3
(a) Uniform random subcarrier allocation; (b) power spectrum density (PSD) of the transmitted signal.
(a)
(b)An OFDM symbol can be considered as the sum of multiple orthogonal signal-carrier signals in the symbol durationT. Each subcarrier is modulated with different transmit data belonging to a Quadrature Amplitude Modulation (QAM) or phase-shift keying (PSK) constellation map. The transmitted time-domain baseband signal of the mth user is expressed by(1)xmt=∑n∑k∈AmdknpTt-nTej2πt-nTfk,where n denotes the number of OFDM symbols. dkn denotes the transmitted data with the kth subcarrier of the nth symbol. T is the OFDM symbol period; pTt-nT is the shaping filter of the transmitter; fk is the frequency of the kth subcarrier.For OFDM modulation, the shaping filter is a time-domain rectangular filter, which includes the duration of cyclic prefix (CP) denoted byTCP. CP is important for OFDM modulation to eliminate the intersymbol interference (ISI) due to multipath wireless channels and is inserted between adjacent OFDM symbols. The shaping filter of the OFDM transmitter can be expressed as(2)pTt=rect⁡tT=1,0≤t≤T,0,otherwise,where T=T0+TCP. T0 is the duration of OFDM symbol except the cyclic prefix.


### 2.3. Target Channel Model

We consider the equivalent baseband models of signal processing in this paper for convenient. Letx represent a particular sequence of OFDM waveforms to be used for transmission, and n represents the additive white Gaussian noise (AWGN). Suppose there are H nonfluctuating far-field targets (according to the Swerling-0 model [35]) in the illuminating area of one RadCom node with distances Rhh=1H and relative velocities of vhh=1H. Correspondingly, the delay and Doppler shift of each target can be expressed as τh=2Rh/c and fD,h=2fCvh/c, respectively, where c is the speed of light and fC is the carrier frequency of OFDM signals.By discarding the cyclic prefix samples in the receiver, the received time-domain signal of themth user can be expressed as(3)ymt=∑h=1Hahxmt-τhej2πfD,ht+wt=∑h=1H∑n∑k∈AmahdknpTt-nT-τh×ej2πt-nT-τhfkej2πfD,ht+wt, where wt is additive white Gaussian noise (AWGN) with zero-mean and variance σ2. ah is the attenuation of the hth target affected by path loss, scattering, and processing gains.


### 2.4. RadCom Node Receiver Subsystem

The received baseband signal is passed to an OFDM demodulator as illustrated in Figure2, which converts the signal from time domain to frequency domain. On account that the information is modulated in frequency domain with OFDM, this essentially acquired the information after channel distortion as(4)d^kn=∫t=nTn+1TytpRt-nTe-j2πt-nTfkdt, where pRt=rect⁡t/T is the matched filter in the receiver corresponding to the shaping filter in the transmitter. For the OFDM modulation, the matched filter and shaping filter have the same form, which has the rectangular window in time domain.Then, the demodulated data is fed into the communication module or radar module alternatively. Note that the demodulation process related to the radar module does not consider any equalization in time domain or in frequency domain. The timing synchronization is the same as the transmitter in order to obtain the time reference. Next we introduce details of our radar signal processing in Section3.


## 2.1. RadCom Network Setup

Figure1 [19] shows a typical RadCom network. Those nodes are capable of maintaining communication links between themselves and maintaining active sensing of the target scene using the backscattered signals. The communication and radar functionalities occur simultaneously. The RadCom signal is used for both communications among RadCom nodes and target localization. Specifically, the RadCom signal is transmitted from the car on the left which establishes a communication link with the car on the upper right. At the same time, this RadCom signal is reflected by some objects, that is, the car on the middle right side. The car on the left receives the reflected signal and estimates the range and velocity of the target by using related signal processing methods. Simultaneously, signals from other RadCom nodes, that is, the car on the bottom right, are received by the car on the left and interfere with the receiver.Figure 1
RadCom network in ITS applications [19].A mechanism similar to general OFDMA is used for multiuser access. Each RadCom node needs to know the instantaneous channel occupancy information when they transmit signals. Instead of using periodical or grouped subcarriers, the idea in this paper is to choose a random set of subcarriers for each node. Nevertheless, the subcarriers allocated to each user are not specified by the user itself entirely but preassigned by the RadCom network protocol and selected by the user with appropriate broadcast protocols. The problem of channel overlap between users can be avoided in this way. In this paper, we focus on the related radar signal processing method. Issues like broadcast protocols can be solved by the existing wireless communication protocols [33].


## 2.2. RadCom Node Transmitter Subsystem

Figure2 presents the internal architecture of a single RadCom node. A channel allocation module corresponding to the subcarrier allocation protocol is introduced in order to provide subcarrier information for both transmitter and receiver of each user. When there are M users, each user is assigned with K randomly selected subcarriers according to a uniform distribution. Let Am denote the set of active subcarrier indices reserved for user m, so that ⋃m=1MAm={1,…,K} and Am∩Am′=⌀. As shown in [34], the random selection of the frequency samples guarantees that the DFT matrix obeys the restricted isometry property (RIP) with high probability, which is necessary for SR-based techniques. The module named Divide is related to the modulation Symbol-Domain method, which is used for eliminating the modulation information while performing radar sensing functions. More details are presented in Section 3.Figure 2
RadCom node architecture.Figure3 shows a case of random selected subcarrier allocation and its corresponding power spectrum of the transmitted signal. In this case, the number of subcarriers is 64, which is one-sixteenth of the number of total available subcarriers.Figure 3
(a) Uniform random subcarrier allocation; (b) power spectrum density (PSD) of the transmitted signal.
(a)
(b)An OFDM symbol can be considered as the sum of multiple orthogonal signal-carrier signals in the symbol durationT. Each subcarrier is modulated with different transmit data belonging to a Quadrature Amplitude Modulation (QAM) or phase-shift keying (PSK) constellation map. The transmitted time-domain baseband signal of the mth user is expressed by(1)xmt=∑n∑k∈AmdknpTt-nTej2πt-nTfk,where n denotes the number of OFDM symbols. dkn denotes the transmitted data with the kth subcarrier of the nth symbol. T is the OFDM symbol period; pTt-nT is the shaping filter of the transmitter; fk is the frequency of the kth subcarrier.For OFDM modulation, the shaping filter is a time-domain rectangular filter, which includes the duration of cyclic prefix (CP) denoted byTCP. CP is important for OFDM modulation to eliminate the intersymbol interference (ISI) due to multipath wireless channels and is inserted between adjacent OFDM symbols. The shaping filter of the OFDM transmitter can be expressed as(2)pTt=rect⁡tT=1,0≤t≤T,0,otherwise,where T=T0+TCP. T0 is the duration of OFDM symbol except the cyclic prefix.


## 2.3. Target Channel Model

We consider the equivalent baseband models of signal processing in this paper for convenient. Letx represent a particular sequence of OFDM waveforms to be used for transmission, and n represents the additive white Gaussian noise (AWGN). Suppose there are H nonfluctuating far-field targets (according to the Swerling-0 model [35]) in the illuminating area of one RadCom node with distances Rhh=1H and relative velocities of vhh=1H. Correspondingly, the delay and Doppler shift of each target can be expressed as τh=2Rh/c and fD,h=2fCvh/c, respectively, where c is the speed of light and fC is the carrier frequency of OFDM signals.By discarding the cyclic prefix samples in the receiver, the received time-domain signal of themth user can be expressed as(3)ymt=∑h=1Hahxmt-τhej2πfD,ht+wt=∑h=1H∑n∑k∈AmahdknpTt-nT-τh×ej2πt-nT-τhfkej2πfD,ht+wt, where wt is additive white Gaussian noise (AWGN) with zero-mean and variance σ2. ah is the attenuation of the hth target affected by path loss, scattering, and processing gains.


## 2.4. RadCom Node Receiver Subsystem

The received baseband signal is passed to an OFDM demodulator as illustrated in Figure2, which converts the signal from time domain to frequency domain. On account that the information is modulated in frequency domain with OFDM, this essentially acquired the information after channel distortion as(4)d^kn=∫t=nTn+1TytpRt-nTe-j2πt-nTfkdt, where pRt=rect⁡t/T is the matched filter in the receiver corresponding to the shaping filter in the transmitter. For the OFDM modulation, the matched filter and shaping filter have the same form, which has the rectangular window in time domain.Then, the demodulated data is fed into the communication module or radar module alternatively. Note that the demodulation process related to the radar module does not consider any equalization in time domain or in frequency domain. The timing synchronization is the same as the transmitter in order to obtain the time reference. Next we introduce details of our radar signal processing in Section3.


## 3. SR-Based Range-Doppler Processing

In this section, we develop a method for jointly estimating the range and Doppler shift based on SR technique in the multiuser scenario. OFDM-based RadCom system was first developed in [19] and an element-wise division technique was proposed for obtaining the channel information. DFT is used to estimate the range and Doppler frequency shift independently. In order to realize radar sensing functions more robustly, a range-Doppler processing framework is constructed combined with SR method.For the scope of this paper, the following assumptions are made:(1)
The two-way propagation time of the reflected signal for the furthest target is smaller than the cyclic prefix duration in order to guarantee the orthogonality between the received signals and the transmitted signals.(2)
The center frequency of the signal is much larger than the total bandwidth, so that the Doppler shift is assumed to be constant over the entire bandwidth.(3)
The position of the target is assumed to be constant during the total integration period; that is, the target’s radial velocity is small enough and the radial displacement can be neglected while processing.(4)
The Doppler shift of the target is much smaller than the subcarrier space, which is also for guaranteeing the orthogonality of the signals as much as possible.With these assumptions, the demodulated symbol of the reflected OFDM signal can be written as(5)d^kn=∑h=1Hahdkne-j2πτhfkej2πfD,hnT+wkn,where wk[n] is the additive noise related to the nth symbol in the kth subcarrier. Let D denote a new matrix with its entries the element-wise division of the received symbols d^kn and transmitted symbols dkn [19], given as(6)D=D0,0D0,1⋯D0,N-1D1,0D1,1⋯D1,N-1⋮⋮⋱⋮DK-1,0DK-1,1⋯DK-1,N-1,where Dk,n=d^k[n]/dk[n]=∑h=1Hahe-j2πτhfkej2πfD,hnT+wk[n]/dk[n].LetX denote a new matrix with its each nonzero element Xτ,fD corresponding to a reflecting target or clutter. The amplitude of each nonzero element represents the reflection strength ah of the hth target, given as(7)Xτ,fD=ah,ifτ=τh,fD=fD,h,0,otherwise.Then, (6) can be represented as(8)D=FKXFNH+W,where FK and FN represent Fourier transform matrices with different sizes of K×K and N×N, respectively. W is the additional noise matrix. ·H denotes the conjugate transpose of a matrix.According to the definition of Kronecker product, (8) can be expressed in vector form, given as(9)vec⁡D=FK⊗FNvec⁡X+vec⁡W,where ⊗ denotes Kronecker product of two matrices.Equation (9) corresponds to the vectorization processing of two-dimensional SR in a traditional manner, that is, in [36]. Although each node occupies all time for communication and sensing, the amount of OFDM symbols are not undersampled. Considering factors of computational efficiency, we only take advantage of SR in one dimension, namely, the range estimation procedure. As for the Doppler offset estimation procedure, the classical spectrum estimation method and a Doppler frequency detector are employed. Formally, performing DFT on each row of matrix D in (8), one has(10)Y=DFN+WFN=FKXFNHFN+WFN=FKX+W~.Thenth column of a matrix is denoted as ·n. Then, one has(11)Yn=FKXn+W~n,n∈1,2,…,N.Considering that the active subcarrier set is assigned byA. There are only a small number of rows in matrix Y to be effective, while other rows correspond to inefficient transmitted data and are invalid after division processing. The number of active subcarriers corresponds to active subcarrier set A that is denoted by KA. Let YA denote the submatrix corresponding to the active subcarrier set A. The Fourier transform matrix becomes FA in the same manner. Hence,(12)YAn=FAXn+W~An,n∈1,2,…,N.In (12), there are N equations. N equals the number of OFDM symbols for integration and is large with a long integration period. To this end, an additional detector is applied to (12) and only a small number of equations are reserved among all N equations.In order to maximize the detection performance, a matched filter is performed on each equation. Here we use symbolsy~, x~, and w~ to indicate the signal components for nth equation in (12), respectively, given as(13a)y~=FAHYAn,(13b)x~=FAHFAXn,(13c)w~=FAHWAn.Then thenth equation in (12) can be written as(14)y~=x~+w~.The detection problem of thekth element in x~ is formulated as(15a)H0:y~k=w~k,(15b)H1:y~k=x~k+w~k.Then, a threshold detector can be used to perform the target detection in each Doppler frequency, namely,(16)∑k∈Auy~k-λ0σ≷H0H11, where u(·) represents unit step function; σ is the variance of the noise after matched filter; and λ0 is the threshold factor that can be used to adjust the threshold to control the detection and false alarm probability. In this paper, a cell average technique is used to estimate the noise variance adaptively, given as(17)σ^=2π∑n=1N∑k=1KAy~k,nNKA.To remove unnecessary dismissal, a smaller threshold factor is used, especially with low signal-to-noise ratios. However, a smaller threshold factor will increase the remaining equations to solve. Since this is only an intermediate step followed by the SR-based solving algorithm, only computational complexity is affected.By this way, the multiple variable estimation problem in (8) becomes at most N parallel one-dimensional estimation process. Since the number of targets is always small, l0 norm of Xn satisfies Xn0≪K. Then, the estimation of Xn can be obtained by solving the following optimization problem:(18)X^n=argminXnXn0s.t.YAn-FAXn2≤σ.There are a wide variety of approaches to solve (18), including greedy algorithms, l1 norm minimization basis pursuit denoising (BPDN), and iterative thresholding [37–39]. In the high noisy environment, BPDN usually performs much better than the others [39]. The Homotopy algorithm can solve the BPDN problem more efficiently with lower computational complexity compared with the classical convex optimization algorithms, especially when the size of the problem is large [36].In the simulation, we use the BPDN algorithm to estimate the sparse vectorX^n. Figure 4 shows the flow chart of the range-Doppler processing. A one-dimensional BPDN algorithm is used in the last step concurrently. As can be seen at the end of Section 4, the threshold factor λ0 can influence the performance of the Doppler frequency detector, especially when SNR is ultralow. In the following, it is assumed that λ0 is small enough for all simulations except the last one concentrated on the detector performance, in order to guarantee that these results are optimal and are not influenced by other factors.Figure 4
The flow chart of the range-Doppler processing.


## 4. Simulation Results and Discussion

In this section, simulation results are presented for performance evaluation. The proposed processing method is compared with the classical processing methods. Section4.1 introduces the simulation scenarios. Sections 4.2 and 4.3 present simulation results of target detection performance without and with multiuser interference in an AWGN environment, respectively. Section 4.4 analyzes the influence of the threshold factor on the performance of the Doppler frequency detector.


### 4.1. Simulation Scenarios

The RadCom system parameters are shown in Table1 as in [18]. The received OFDM symbols are processed with the range-Doppler estimation algorithm without performing any previous channel equalization or decision.Table 1
OFDM RadCom system parameters.
Parameter
Value
Carrier frequency
5.9 GHz
Subcarrier spacing
90.909 kHz
OFDM symbol length
11 us
Cyclic prefix length
1.375 us
Bandwidth
93.1 MHz
Symbol number for integration
256The OFDM signal fulfills certain requirements for division operation in (6) in order to be correct. Specifically, deorthogonalization needs to be avoided to make sure that d^kn is correctly aligned to the corresponding dkn. In this case, the time delay τh is smaller than TCP, which corresponds to a maximum target distance of about 206 m. Also, the maximum Doppler shift is required to stay smaller than the subcarrier spacing. When the radial velocity of the target is 200 km/h, the Doppler shift is approximately 2.2 kHz, which is only 2.4% of the subcarrier spacing. In the following simulations, the distance and radial velocity of targets are assumed to be in the range within (0, 200] m and [-2.2,2.2] kHz separately for unambiguity and guaranteeing of orthogonality, and all targets are located on the grids of range-Doppler processing. According to the OFDM system parameterization, the range resolution is about 1.61 m, and the Doppler frequency resolution is about 315 Hz.


### 4.2. Radar Performance without Interference

When there is no interference, that is, only one node in active operating mode, the radar performance is only influenced by SNR and the number of active subcarriers.First, it is assumed that only one target exists with delay and Doppler shift randomly locates in the assumed unambiguous region. The peak-to-side-lobe ratio (PSLR), which describes the ratio between the main peak and maximum side-lobe value, is used for performance analysis with different SNRs. The side-lobe value is mainly caused by Fourier side-lobes since the modulated information is eliminated by using the modulation Symbol-Domain method [19]. Periodogram is employed with classical modulation Symbol-Domain method. Since works in [19] have proved that the modulation Symbol-Domain method is superior to the matched filter with OFDM waveform under the assumed scenes, we only consider the classical modulation Symbol-Domain method for performance comparison. Hereinafter, the classical modulation Symbol-Domain method is expressed as “Symbol-Domain” and the proposed SR-based method is expressed as “Symbol-Domain SR” for simplicity. All the results are obtained by averaging over 1000 independent trials.Figure5 presents the PSLR versus SNRs. Different lines present the results obtained by using different methods with different number of subcarriers. It is seen that, in the double logarithmic representation, the PSLR of the proposed Symbol-Domain SR method increases linearly with SNR. PSLRs with less subcarrier number are slightly higher. This phenomenon is mainly caused by the lower noise level with less sampled data when the number of subcarriers is smaller. On the contrary, all PSLRs of classical Symbol-Domain method with partial subcarriers have a performance bottleneck. That is, when the SNRs of the received signal increases, the PSLRs tend to be constant. In addition, when the subcarrier number decreases, the PSLR of classical method decreases, which is contrary to the proposed method. When all available subcarriers are used by a single user, the performance of Symbol-Domain SR method is equivalent to the classical Symbol-Domain method.Figure 5
Achievable peak-to-side-lobe ratios of different methods in a noisy single user scenario.Figure6 shows the range and Doppler shift estimation of both Symbol-Domain and Symbol-Domain SR methods in one experiment of single target with SNR being −20 dB and the number of subcarriers equals 128. Range and Doppler grid corresponding to the sampling number in their respective dimensions are employed to represent the relative estimation performance. It is observed that the Symbol-Domain method has higher side-lobes compared to that achieved by using the Symbol-Domain SR method. Meanwhile, the side-lobes are mainly located in the range dimension. The difference of range side-lobes is mainly caused by the partial use of subcarriers, which is equivalent to undersampling in frequency domain corresponding to the range dimension.Figure 6
Range and Doppler estimation of single target when SNR = −20 dB. (a) Symbol-Domain and (b) Symbol-Domain SR.
(a)
(b)In order to verify the performance with multiple targets, the receiver operating characteristic (ROC) is computed in simulation with five targets having the same SNRs. The first two targets belong to the same range bin. The other two targets belong to another Doppler bin, and the fifth target is chosen to have random range and Doppler shift different from the first four. All five targets are located randomly in the assumed unambiguous range. For convenient analysis, the SNR is chosen to be −33 dB, which provides clear results. Since the first target and the second target are exchangeable, and the same to the third target and the fourth target, we only consider the detection of three targets, that is, the first, the third, and the fifth target. All the results are obtained by averaging over 1000 independent trials.Figure7 shows the ROC curves for different parameters. In Figures 7(a) and 7(b), ROC curves are presented for different targets when the number of subcarriers is 64 and 128. As can be seen that the performance of the third target is much worse, this corresponds to the two targets with the same range bin. As for the first and the fifth target, the ROC curves behave similarly. In Figures 7(c) and 7(d), ROC curves are presented for different subcarrier numbers with the first and the third targets. For the ROCs of the first target, which corresponds to the two targets with the same Doppler bin, there is not obvious performance reduction. However, when the number of subcarriers decreases, the detection performance of the third target reduces. The main reason is that the high side-lobes are located in the same range bin relative to the real target. In a word, targets with the same range bin may cause shadowing effect to each other and result in performance reduction.Figure 7
Receiver operating characteristic (ROC) curves for targets with different number of subcarriers.
(a)
K
A
=
64
(b)
K
A
=
128
(c)
The first target
(d)
The third target


### 4.3. Radar Performance with Multiuser Interference

In order to further investigate the performance in the presence of multiuser interference, simulations are performed with various interference levels and different interference parameters.In order to investigate the influence of imperfect timing and carrier frequency synchronization, simulations with different timing shift and different carrier frequency shifts are performed. First, the signal-to-interference ratio (SIR) is fixed at −40 dB. Different timing and carrier frequency shifts are used to illustrate the influences of the imperfect synchronization intuitively. Then, different SIRs are considered with several timing and carrier frequency shifts. All the results are obtained by averaging over 1000 independent trials.Figure8(a) shows simulation results for the PSLR dependent on the timing shift of the interferer, while the carrier frequency is assumed to be accurate. When the time shift is smaller than the duration of the cyclic prefix, there is no PSLR reduction. In this case, the duration of cyclic prefix is 0.125T. For higher timing shifts, a PSLR drop occurs. This is caused by the fact that the orthogonality of the OFDM symbols among different users is damaged. As for the classical Symbol-Domain method, the effect of deorthogonalization does not appear. It is because that the high side-lobes are mainly caused by the undersampling, instead of the deorthogonalization.Figure 8
Peak-to-side-lobe ratio with multiuser interference when timing offset exists. (a) PSLR versus different relative timing offset when SIR = −40 dB. (b) PSLR versus different SIRs.
(a)
(b)Figure8(b) shows the PSLR versus the signal-to-interference ratio and the timing shift. It can be seen that a slight timing shift leads to an obvious performance reduction. When the timing shift increases, the performance is decreased with the increase of the SIR. This behavior is the same to the Symbol-Domain and Symbol-Domain SR methods but with different levels.Similarly, Figure9(a) shows the simulation results for the PSLR dependent on the frequency shift of the interference while the timing synchronization is assumed to be perfect. The achievable PSLR of the proposed method degrades with the increasing frequency shift of the interference. When the frequency shift is about 4500 Hz, which corresponds to a radial velocity of about 412 km/h, the PSLR degradation is nearly 20 dB. Nevertheless, the PSLR of Symbol-Domain SR method still outperforms the classical method nearly 17 dB. Figure 9(b) shows the PLSR as a function of the signal-to-interference ratio and the frequency shift. The curves show the same characteristics as the analysis in Figure 8(b) for timing shift analysis.Figure 9
Peak-to-side-lobe ratio with multiuser interference when carrier frequency offset exists. (a) PSLR versus different frequency offset when SIR = −40 dB. (b) PSLR versus different SIRs.
(a)
(b)


### 4.4. Sensitivity of Threshold Factor for Doppler Frequency Detector

We assume that there are five targets with the same signal-to-noise ratio but located with completely random range and Doppler frequency shifts in the assumed unambiguity ranges.Figure10 shows the variations of the detection probability and false alarm probability versus the threshold factors for different signal-to-noise ratios when the subcarrier number is 64. It is seen that the change of the SNR does not influence the false alarm probability. But when the SNR increases, the detection probability behaves quite differently. When the threshold factor λ0 is selected to make the detection probability equal to 0.95, false alarm probabilities are different at different SNRs. When the SNR equals −35 dB, the false alarm probability is only 0.0321. This indicates that only 3.21 percent of the total computational burden is extra added. However, when the SNR equals −40 dB and −45 dB, the additional computational burden increases to 83.87 percent and 93.18 percent, respectively.Figure 10
Detection and false alarm probability versus threshold factorλ0.In a word, when the SNR is ultralow, the Doppler frequency detector has no effect on decreasing calculation amount. Otherwise, when the SNR is high, the curves of detection probability and false alarm probability separate in a wide range of the threshold factor. An appropriate value of the threshold factor can be chosen in order to exclude the frequencies with no target. According to the simulation results, for a certain detection probability, the threshold factor is related to the SNR directly. Applicable approaches of estimating actual SNR are needed for choosing the correct threshold factor value, but it is beyond the scope of this paper.


## 4.1. Simulation Scenarios

The RadCom system parameters are shown in Table1 as in [18]. The received OFDM symbols are processed with the range-Doppler estimation algorithm without performing any previous channel equalization or decision.Table 1
OFDM RadCom system parameters.
Parameter
Value
Carrier frequency
5.9 GHz
Subcarrier spacing
90.909 kHz
OFDM symbol length
11 us
Cyclic prefix length
1.375 us
Bandwidth
93.1 MHz
Symbol number for integration
256The OFDM signal fulfills certain requirements for division operation in (6) in order to be correct. Specifically, deorthogonalization needs to be avoided to make sure that d^kn is correctly aligned to the corresponding dkn. In this case, the time delay τh is smaller than TCP, which corresponds to a maximum target distance of about 206 m. Also, the maximum Doppler shift is required to stay smaller than the subcarrier spacing. When the radial velocity of the target is 200 km/h, the Doppler shift is approximately 2.2 kHz, which is only 2.4% of the subcarrier spacing. In the following simulations, the distance and radial velocity of targets are assumed to be in the range within (0, 200] m and [-2.2,2.2] kHz separately for unambiguity and guaranteeing of orthogonality, and all targets are located on the grids of range-Doppler processing. According to the OFDM system parameterization, the range resolution is about 1.61 m, and the Doppler frequency resolution is about 315 Hz.


## 4.2. Radar Performance without Interference

When there is no interference, that is, only one node in active operating mode, the radar performance is only influenced by SNR and the number of active subcarriers.First, it is assumed that only one target exists with delay and Doppler shift randomly locates in the assumed unambiguous region. The peak-to-side-lobe ratio (PSLR), which describes the ratio between the main peak and maximum side-lobe value, is used for performance analysis with different SNRs. The side-lobe value is mainly caused by Fourier side-lobes since the modulated information is eliminated by using the modulation Symbol-Domain method [19]. Periodogram is employed with classical modulation Symbol-Domain method. Since works in [19] have proved that the modulation Symbol-Domain method is superior to the matched filter with OFDM waveform under the assumed scenes, we only consider the classical modulation Symbol-Domain method for performance comparison. Hereinafter, the classical modulation Symbol-Domain method is expressed as “Symbol-Domain” and the proposed SR-based method is expressed as “Symbol-Domain SR” for simplicity. All the results are obtained by averaging over 1000 independent trials.Figure5 presents the PSLR versus SNRs. Different lines present the results obtained by using different methods with different number of subcarriers. It is seen that, in the double logarithmic representation, the PSLR of the proposed Symbol-Domain SR method increases linearly with SNR. PSLRs with less subcarrier number are slightly higher. This phenomenon is mainly caused by the lower noise level with less sampled data when the number of subcarriers is smaller. On the contrary, all PSLRs of classical Symbol-Domain method with partial subcarriers have a performance bottleneck. That is, when the SNRs of the received signal increases, the PSLRs tend to be constant. In addition, when the subcarrier number decreases, the PSLR of classical method decreases, which is contrary to the proposed method. When all available subcarriers are used by a single user, the performance of Symbol-Domain SR method is equivalent to the classical Symbol-Domain method.Figure 5
Achievable peak-to-side-lobe ratios of different methods in a noisy single user scenario.Figure6 shows the range and Doppler shift estimation of both Symbol-Domain and Symbol-Domain SR methods in one experiment of single target with SNR being −20 dB and the number of subcarriers equals 128. Range and Doppler grid corresponding to the sampling number in their respective dimensions are employed to represent the relative estimation performance. It is observed that the Symbol-Domain method has higher side-lobes compared to that achieved by using the Symbol-Domain SR method. Meanwhile, the side-lobes are mainly located in the range dimension. The difference of range side-lobes is mainly caused by the partial use of subcarriers, which is equivalent to undersampling in frequency domain corresponding to the range dimension.Figure 6
Range and Doppler estimation of single target when SNR = −20 dB. (a) Symbol-Domain and (b) Symbol-Domain SR.
(a)
(b)In order to verify the performance with multiple targets, the receiver operating characteristic (ROC) is computed in simulation with five targets having the same SNRs. The first two targets belong to the same range bin. The other two targets belong to another Doppler bin, and the fifth target is chosen to have random range and Doppler shift different from the first four. All five targets are located randomly in the assumed unambiguous range. For convenient analysis, the SNR is chosen to be −33 dB, which provides clear results. Since the first target and the second target are exchangeable, and the same to the third target and the fourth target, we only consider the detection of three targets, that is, the first, the third, and the fifth target. All the results are obtained by averaging over 1000 independent trials.Figure7 shows the ROC curves for different parameters. In Figures 7(a) and 7(b), ROC curves are presented for different targets when the number of subcarriers is 64 and 128. As can be seen that the performance of the third target is much worse, this corresponds to the two targets with the same range bin. As for the first and the fifth target, the ROC curves behave similarly. In Figures 7(c) and 7(d), ROC curves are presented for different subcarrier numbers with the first and the third targets. For the ROCs of the first target, which corresponds to the two targets with the same Doppler bin, there is not obvious performance reduction. However, when the number of subcarriers decreases, the detection performance of the third target reduces. The main reason is that the high side-lobes are located in the same range bin relative to the real target. In a word, targets with the same range bin may cause shadowing effect to each other and result in performance reduction.Figure 7
Receiver operating characteristic (ROC) curves for targets with different number of subcarriers.
(a)
K
A
=
64
(b)
K
A
=
128
(c)
The first target
(d)
The third target


## 4.3. Radar Performance with Multiuser Interference

In order to further investigate the performance in the presence of multiuser interference, simulations are performed with various interference levels and different interference parameters.In order to investigate the influence of imperfect timing and carrier frequency synchronization, simulations with different timing shift and different carrier frequency shifts are performed. First, the signal-to-interference ratio (SIR) is fixed at −40 dB. Different timing and carrier frequency shifts are used to illustrate the influences of the imperfect synchronization intuitively. Then, different SIRs are considered with several timing and carrier frequency shifts. All the results are obtained by averaging over 1000 independent trials.Figure8(a) shows simulation results for the PSLR dependent on the timing shift of the interferer, while the carrier frequency is assumed to be accurate. When the time shift is smaller than the duration of the cyclic prefix, there is no PSLR reduction. In this case, the duration of cyclic prefix is 0.125T. For higher timing shifts, a PSLR drop occurs. This is caused by the fact that the orthogonality of the OFDM symbols among different users is damaged. As for the classical Symbol-Domain method, the effect of deorthogonalization does not appear. It is because that the high side-lobes are mainly caused by the undersampling, instead of the deorthogonalization.Figure 8
Peak-to-side-lobe ratio with multiuser interference when timing offset exists. (a) PSLR versus different relative timing offset when SIR = −40 dB. (b) PSLR versus different SIRs.
(a)
(b)Figure8(b) shows the PSLR versus the signal-to-interference ratio and the timing shift. It can be seen that a slight timing shift leads to an obvious performance reduction. When the timing shift increases, the performance is decreased with the increase of the SIR. This behavior is the same to the Symbol-Domain and Symbol-Domain SR methods but with different levels.Similarly, Figure9(a) shows the simulation results for the PSLR dependent on the frequency shift of the interference while the timing synchronization is assumed to be perfect. The achievable PSLR of the proposed method degrades with the increasing frequency shift of the interference. When the frequency shift is about 4500 Hz, which corresponds to a radial velocity of about 412 km/h, the PSLR degradation is nearly 20 dB. Nevertheless, the PSLR of Symbol-Domain SR method still outperforms the classical method nearly 17 dB. Figure 9(b) shows the PLSR as a function of the signal-to-interference ratio and the frequency shift. The curves show the same characteristics as the analysis in Figure 8(b) for timing shift analysis.Figure 9
Peak-to-side-lobe ratio with multiuser interference when carrier frequency offset exists. (a) PSLR versus different frequency offset when SIR = −40 dB. (b) PSLR versus different SIRs.
(a)
(b)


## 4.4. Sensitivity of Threshold Factor for Doppler Frequency Detector

We assume that there are five targets with the same signal-to-noise ratio but located with completely random range and Doppler frequency shifts in the assumed unambiguity ranges.Figure10 shows the variations of the detection probability and false alarm probability versus the threshold factors for different signal-to-noise ratios when the subcarrier number is 64. It is seen that the change of the SNR does not influence the false alarm probability. But when the SNR increases, the detection probability behaves quite differently. When the threshold factor λ0 is selected to make the detection probability equal to 0.95, false alarm probabilities are different at different SNRs. When the SNR equals −35 dB, the false alarm probability is only 0.0321. This indicates that only 3.21 percent of the total computational burden is extra added. However, when the SNR equals −40 dB and −45 dB, the additional computational burden increases to 83.87 percent and 93.18 percent, respectively.Figure 10
Detection and false alarm probability versus threshold factorλ0.In a word, when the SNR is ultralow, the Doppler frequency detector has no effect on decreasing calculation amount. Otherwise, when the SNR is high, the curves of detection probability and false alarm probability separate in a wide range of the threshold factor. An appropriate value of the threshold factor can be chosen in order to exclude the frequencies with no target. According to the simulation results, for a certain detection probability, the threshold factor is related to the SNR directly. Applicable approaches of estimating actual SNR are needed for choosing the correct threshold factor value, but it is beyond the scope of this paper.


## 5. Conclusions

In this paper, a simple multiuser access scheme with a random subcarrier allocation mechanism has been investigated in RadCom networks. The corresponding SR-based signal processing method is derived. Instead of allocating subcarriers periodically or sequentially with blocks, the proposed scheme fully utilizes the available bandwidth for radar sensing in a completely random manner. Since the total bandwidth occupied by each user does not decrease, the accuracy of radar sensing is the same as the traditional OFDM radar. A parallel structured radar signal processing framework is proposed with a Doppler frequency detector to reduce computational complexity.The advantage of the proposed scheme is that it introduces no range or Doppler ambiguity and allows more users to work simultaneously in the same bandwidth compared with the traditional interleaved subcarrier allocation manner. Simulation results show that the proposed method based on SR is superior to the classical Symbol-Domain method in all SNRs with/without multiuser interferences in the assumed unambiguity ranges. The Doppler frequency detector is highly effective for most SNRs, except when the SNR is ultralow. The scheme proposed in this paper allows more users to work simultaneously without additional bandwidth occupation. With the increasingly crowded spectrum, this can help to further develop integrated RadCom systems in multiuser scenarios, for example, intelligent transportation systems for road safety with high system efficiency.



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*Source: 6528956-2017-04-20.xml*