# A CPW-Fed Dual-Band-Notched Antenna with Sharp Skirt Selectivity for UWB Applications

Authors: Dacheng Dong; Shaojian Chen; Zhouying Liao; Gui Liu
Journal: International Journal of Antennas and Propagation
 (2014)

---

## Abstract

A coplanar waveguide- (CPW-) fed dual-band-notched antenna with sharp skirt selectivity for ultrawideband (UWB) applications is presented. The proposed antenna is composed of a radiant patch with a C-shaped slot and a C-shaped stub on the back surface of the substrate. By using the C-shaped slot and the C-shaped stub, dual-band-notched characteristics can be generated. In this way, a more practical and effective approach to design an UWB antenna with sharp notched-band-edge selectivity is developed. The measurement results show dual notched bands of 4.96–5.42 GHz and 5.71–5.91 GHz, which can reject the interference between IEEE 802.11a bands (5.15–5.35 GHz and 5.725–5.825 GHz) and UWB systems. The fabricated antenna shows good omnidirectional radiation patterns with acceptable gain and group delay.


---

## Body

## 1. Introduction

Ultrawideband (UWB) technology has recently become one of the most promising candidates for short-range high-bandwidth indoor and outdoor wireless communications systems. Since the UWB systems occupy an extremely wide band from 3.1 to 10.6 GHz, it is necessary to reject the interference with the existing wireless local area network (WLAN) for IEEE 802.11a operating at 5.15–5.35 GHz and 5.725–5.825 GHz. As a critical component of an UWB system, band-notched UWB antennas have been widely investigated [1–12]. Numerous techniques have been proposed to realize band-notched function such as utilizing parasitic elements [1], defected ground structure [2], T-shaped stub embedded in the slot [3], modified split-ring resonator (SRR), and many kinds of slots, such as circle-like slot [4], F-shaped slot [5], T-shaped slot [6], E-shaped slot [7], C-shaped slot [8], inverted V-shaped slot [9], inverted S-shaped slot [10], inverted T-shaped slot [11], and Π-shaped slot [12].However, most band-notched antennas cannot provide sharp notched-band-edge selectivity and dual-band-notched characteristics for IEEE 802.11a, which results in the fact that the entire 5-6 GHz frequency band has been completely rejected [13]. The signal contained in the frequency band of 5.35–5.725 GHz is also rejected, which results in severe system performance degradation. Several approaches have been proposed to achieve sharp band-notched characteristics, for instance, inserting a half-wavelength C-shaped slot in the patch and adding two half-wavelength stepped impedance resonators around the feed line [14], slitting an open-ended quarter-wavelength split slot on the back of the feed and a short-ended half-wavelength split-ring slot near the stepped slot [15], using double open-circuited stubs [16], and employing a pair of Y-shaped strips to the annular ring and an inverted V-shaped slot on the patch [17]. However, few of the reported notch-band UWB antennas with sharp skirt selectivity could just cover 5.15–5.35 GHz and 5.725–5.875 GHz [14].To realize compact UWB system, planar dipole antennas can be a good candidate because of their attractive merits such as compact size, low cost, ease of fabrication, and easy integration with feed network. Several novel planar dipole antenna structures have been proposed to widen the impedance matching bandwidth [18–22]. Cappelletti et al. present a drop-shaped dipole antenna which can be used to realize compact array antennas or to reduce the spurious radiation level in the direction of feeding line [18]. A planar dipole UWB antenna with two semielliptical-ended arms connected by a shorting bridge is proposed to achieve enhanced impedance and gain performance [19]. Printed dipole antenna with integrated balun provides wideband impedance matching with miniature size [20]. In [21], a novel wideband balanced loop-dipole composite antenna with end-fire radiation is presented. The measured impedance bandwidth is 129% (from 3.26 to 15 GHz). In [22], a differentially fed magnetoelectric dipole (ME dipole) is designed by introducing two slots in the dipole arms so providing an ultrawideband impedance matching. However, these antennas often suffer from high profiles or the structures are too complicated to be fabricated and assembled.In this study, a novel band-notched UWB antenna with sharp selectivity is presented. The proposed antenna consists of a radiant patch with an embedded C-shaped slot and a C-shaped stub on the back surface of the substrate. The desired notched band can be easily achieved by properly designing a C-shaped slot and a C-shaped stub. In this way, two stop bands with sharp skirt selectivity can be obtained.This paper is organized as follows. The antenna structure and details of the parameter optimizations are introduced in Section2. In addition, the surface current distributions are also provided and analyzed. Section 3 shows the measurement results of the proposed antenna, namely, its reflection coefficient, radiation patterns, and gain. Finally, Section 4 presents the conclusion for this research.


## 2. Antenna Configuration

The geometry of the proposed dual-band-notched UWB antenna is depicted in Figure1. The antenna is fabricated on a 38 mm × 44 mm × 0.8 mm F4B substrate with relative permittivity 2.55, loss tan 0.003, and thickness of 0.8 mm. The antenna consists of a radiator with a C-shaped slot, a taped CPW line on the front of the substrate, and a C-shaped stub on the back surface of the substrate. The key innovation in the proposed design is to use both the C-shaped slot and the C-shaped stub to achieve dual-notched-band characteristics with sharp skirt selectivity. The proposed antenna is fed by the coplanar waveguide (CPW) due to its significant advantages compared to microstrip-fed lines, for instance, unipolar configuration, easy integration, compact size, and ease of manufacture. Furthermore, the tapered CPW could improve the impedance matching in a wide frequency band.Geometry of the proposed antenna. (a) Structure and (b) photographs.
(a)
(b)


## 3. Results and Discussions

### 3.1. Return Loss

Figure2 shows the return loss of the proposed antenna under three structures: (1) Structure 1: without the slot and the stub, (2) Structure 2: with the slot but without the stub, and (3) Structure 3: with both the slot and the stub. As can be observed from Figure 2, the slot introduces a single-band-notched function, while the dual-band-notched function is achieved by employing both the slot and the stub.Figure 2
Simulated return loss of the proposed antenna with three configurations of slot and stub.To further investigate the effect of the stub on the return loss of the proposed antenna, various lengths of the stub have been studied and optimized. Figure3 shows the return loss of the proposed antenna with different lengths of the parameter SL1. From this figure, it appears that, by adjusting the length of the parameter SL1, the resonance frequency of the rejected band can be properly tuned.Figure 3
Simulated return loss of the proposed antenna with different values ofSL1.As illustrated in Figure4, the length of the C-shaped slot has a great effect on the lower notched frequency band, while it does not affect the higher notched frequency band.Figure 4
Simulated return loss of the proposed antenna with different values ofSL3.As shown in Figure5, it is observed that, when the parameter R increases from 10.8 mm to 11.2 mm, the center frequencies of the dual-notched-band increase. Therefore, the center frequencies of the dual-notched-band are controllable by varying the parameter R.Figure 5
Simulated return loss of the proposed antenna with different values ofR.Figure6 shows the simulated and measured return loss characteristics of the proposed antenna. Slight discrepancy between the measurement and the simulation results could be due to the effects of the SMA connector, which has not been included in the numerical model. The −10 dB bandwidth is from 3.1 to 10.6 GHz with sharp notched-band-edge selectivity (4.96–5.42 GHz and 5.71–5.91 GHz).Figure 6
Simulated and measured return loss of the proposed antenna.The optimized parameters of the proposed antenna are the following:L1 = 44 mm, L2 = 19 mm, L3 = 18 mm, L4 = 4 mm, L5 = 2.5 mm, W1 = 38 mm, W2 = 18 mm, W3 = 8.5 mm, SL1 = 19 mm, R = 11 mm, SL2 = 3.7 mm, SL3 = 9 mm, SL4 = 4.7 mm, SL5 = 3.7 mm, SW1 = 4.8 mm, SW2 = 0.5 mm, SW3 = 4.2 mm, and SW4 = 2.6 mm.


### 3.2. Current Distribution

Figure7 illustrates the surface current density computed at the center frequencies of the two notched-bands. As can be observed in Figure 7(a), for the lower-frequency notch (4.96–5.42 GHz), the current density is concentrated close to the C-shaped slot, while Figure 7(b) shows that the current is primarily concentrated around the C-shaped stub for the upper-frequency band (5.71–5.91 GHz).Simulated surface current distributions of the proposed antenna at different frequencies. (a) 5.2 GHz and (b) 5.8 GHz.
(a)
(b)In order to investigate the radiation mechanisms of the notched-band elements, simulated vector current distributions at both notched frequencies (5.2 GHz and 5.8 GHz) are illustrated in Figure8. As shown in Figure 8(a) for 5.2 GHz, the currents flow in the opposite direction along the inner and outer sides of the C-shaped slot. Therefore, the resultant fields cancel each other and consequently the antenna does not radiate electromagnetic energy in the space. Thus, the C-shaped slot can be used to filter out the narrower band emissions. As it can be seen from Figure 8(b), due to the symmetry of the C-shaped stub, the directions of the surface currents along the y-direction on the C-shaped stub are opposite to each other. Therefore, the resultant fields are canceled out and high field attenuation is obtained at the notched frequency. Thus, the proposed antenna does not radiate efficiently around the filter structure at the higher notched frequency.Simulated vector current distributions at different notch frequencies. (a) 5.2 GHz and (b) 5.8 GHz.
(a)
(b)


### 3.3. Radiation Patterns and Gain

Figure9 shows the measured normalized far field radiation patterns in E-plane (xz-plane, spherical angle phi = 0°) and H-plane (xy-plane, spherical angle theta = 90°) at 5.5 GHz, 7 GHz, and 10 GHz, respectively. As can be seen from Figure 9(a), two nulls are observed in the antenna broadside direction at the frequencies of 7 GHz and 10 GHz. The main reason for these two nulls is that, as the frequency increases, the levels of the higher order modes and of the cross-polarization increase too. However, it can be observed that the H-plane patterns are almost omnidirectional for the three considered frequencies.Normalized radiation patterns of the proposed antenna for the three different frequencies taken into consideration: (a) E-plane and (b) H-plane.
(a)
(b)The measured antenna peak gain, reported in Figure10, shows two significant gain decrements at about 5.3 GHz and 5.8 GHz, which confirm the filtering effects. For the other frequencies outside the notched bands, a relatively flat gain is observed over the entire UWB band.Figure 10
Measured peak gain of the proposed antenna.


### 3.4. Group Delay Characteristics

As shown in the previous sections, the proposed antenna exhibits ultrawideband characteristics in the frequency domain. For UWB systems, the time-domain response is also a critical feature [18]. Group delay is a very important parameter of time-domain analysis. It is desirable to keep a constant group delay over the entire frequency band to avoid undesirable distortion of the radiated and received pulses. To evaluate the group delay of the UWB systems, a pair of identical proposed antennas is placed face to face at a distance of 30 cm. As shown in Figure 11, the variation of the group delay, computed by means of the scattering parameter S21, is less than 560 ps with the average of 1.1 ns across the whole UWB frequency band except at both notched bands. In both notched bands, the presence of the band-notch filters deteriorates the radiation performance and the impedance matching, which results in inaccurate and negative group delay. Since the proposed antenna shows an acceptable group delay in the transmission of UWB signals, it is suitable for the UWB communication applications.Figure 11
Group delay of the proposed antenna systems.


## 3.1. Return Loss

Figure2 shows the return loss of the proposed antenna under three structures: (1) Structure 1: without the slot and the stub, (2) Structure 2: with the slot but without the stub, and (3) Structure 3: with both the slot and the stub. As can be observed from Figure 2, the slot introduces a single-band-notched function, while the dual-band-notched function is achieved by employing both the slot and the stub.Figure 2
Simulated return loss of the proposed antenna with three configurations of slot and stub.To further investigate the effect of the stub on the return loss of the proposed antenna, various lengths of the stub have been studied and optimized. Figure3 shows the return loss of the proposed antenna with different lengths of the parameter SL1. From this figure, it appears that, by adjusting the length of the parameter SL1, the resonance frequency of the rejected band can be properly tuned.Figure 3
Simulated return loss of the proposed antenna with different values ofSL1.As illustrated in Figure4, the length of the C-shaped slot has a great effect on the lower notched frequency band, while it does not affect the higher notched frequency band.Figure 4
Simulated return loss of the proposed antenna with different values ofSL3.As shown in Figure5, it is observed that, when the parameter R increases from 10.8 mm to 11.2 mm, the center frequencies of the dual-notched-band increase. Therefore, the center frequencies of the dual-notched-band are controllable by varying the parameter R.Figure 5
Simulated return loss of the proposed antenna with different values ofR.Figure6 shows the simulated and measured return loss characteristics of the proposed antenna. Slight discrepancy between the measurement and the simulation results could be due to the effects of the SMA connector, which has not been included in the numerical model. The −10 dB bandwidth is from 3.1 to 10.6 GHz with sharp notched-band-edge selectivity (4.96–5.42 GHz and 5.71–5.91 GHz).Figure 6
Simulated and measured return loss of the proposed antenna.The optimized parameters of the proposed antenna are the following:L1 = 44 mm, L2 = 19 mm, L3 = 18 mm, L4 = 4 mm, L5 = 2.5 mm, W1 = 38 mm, W2 = 18 mm, W3 = 8.5 mm, SL1 = 19 mm, R = 11 mm, SL2 = 3.7 mm, SL3 = 9 mm, SL4 = 4.7 mm, SL5 = 3.7 mm, SW1 = 4.8 mm, SW2 = 0.5 mm, SW3 = 4.2 mm, and SW4 = 2.6 mm.


## 3.2. Current Distribution

Figure7 illustrates the surface current density computed at the center frequencies of the two notched-bands. As can be observed in Figure 7(a), for the lower-frequency notch (4.96–5.42 GHz), the current density is concentrated close to the C-shaped slot, while Figure 7(b) shows that the current is primarily concentrated around the C-shaped stub for the upper-frequency band (5.71–5.91 GHz).Simulated surface current distributions of the proposed antenna at different frequencies. (a) 5.2 GHz and (b) 5.8 GHz.
(a)
(b)In order to investigate the radiation mechanisms of the notched-band elements, simulated vector current distributions at both notched frequencies (5.2 GHz and 5.8 GHz) are illustrated in Figure8. As shown in Figure 8(a) for 5.2 GHz, the currents flow in the opposite direction along the inner and outer sides of the C-shaped slot. Therefore, the resultant fields cancel each other and consequently the antenna does not radiate electromagnetic energy in the space. Thus, the C-shaped slot can be used to filter out the narrower band emissions. As it can be seen from Figure 8(b), due to the symmetry of the C-shaped stub, the directions of the surface currents along the y-direction on the C-shaped stub are opposite to each other. Therefore, the resultant fields are canceled out and high field attenuation is obtained at the notched frequency. Thus, the proposed antenna does not radiate efficiently around the filter structure at the higher notched frequency.Simulated vector current distributions at different notch frequencies. (a) 5.2 GHz and (b) 5.8 GHz.
(a)
(b)


## 3.3. Radiation Patterns and Gain

Figure9 shows the measured normalized far field radiation patterns in E-plane (xz-plane, spherical angle phi = 0°) and H-plane (xy-plane, spherical angle theta = 90°) at 5.5 GHz, 7 GHz, and 10 GHz, respectively. As can be seen from Figure 9(a), two nulls are observed in the antenna broadside direction at the frequencies of 7 GHz and 10 GHz. The main reason for these two nulls is that, as the frequency increases, the levels of the higher order modes and of the cross-polarization increase too. However, it can be observed that the H-plane patterns are almost omnidirectional for the three considered frequencies.Normalized radiation patterns of the proposed antenna for the three different frequencies taken into consideration: (a) E-plane and (b) H-plane.
(a)
(b)The measured antenna peak gain, reported in Figure10, shows two significant gain decrements at about 5.3 GHz and 5.8 GHz, which confirm the filtering effects. For the other frequencies outside the notched bands, a relatively flat gain is observed over the entire UWB band.Figure 10
Measured peak gain of the proposed antenna.


## 3.4. Group Delay Characteristics

As shown in the previous sections, the proposed antenna exhibits ultrawideband characteristics in the frequency domain. For UWB systems, the time-domain response is also a critical feature [18]. Group delay is a very important parameter of time-domain analysis. It is desirable to keep a constant group delay over the entire frequency band to avoid undesirable distortion of the radiated and received pulses. To evaluate the group delay of the UWB systems, a pair of identical proposed antennas is placed face to face at a distance of 30 cm. As shown in Figure 11, the variation of the group delay, computed by means of the scattering parameter S21, is less than 560 ps with the average of 1.1 ns across the whole UWB frequency band except at both notched bands. In both notched bands, the presence of the band-notch filters deteriorates the radiation performance and the impedance matching, which results in inaccurate and negative group delay. Since the proposed antenna shows an acceptable group delay in the transmission of UWB signals, it is suitable for the UWB communication applications.Figure 11
Group delay of the proposed antenna systems.


## 4. Conclusion

In this paper, a dual-notched-band antenna with sharp notched-band-edge selectivity has been proposed. By using the slot in the radiator and the stub on the back surface of the substrate, dual-notched-band functions are realized. Specifically, measured results show that the intermediate frequency range between 5.43 and 5.7 GHz can be utilized with our proposed antenna, while it is rejected by other WLAN band-notched UWB antennas. Furthermore, the proposed antenna has demonstrated good omnidirectional radiation pattern, acceptable gain, and group delay. Consequently, the proposed antenna could be a good candidate for the UWB applications.



---

*Source: 629387-2014-06-23.xml*