# Structural Parameter Optimization of a Tubular Permanent-Magnet Linear Machine for Regenerative Suspension

Authors: Dongsheng Lu; Hailong Zhang; Jian Liu; Enrong Wang
Journal: Shock and Vibration
 (2019)

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## Abstract

The regenerative suspension can effectively recover the vibration potential energy of the vehicle suspension, thus has broad prospects in application. In this paper, a tubular permanent-magnet linear motor (TPMLM) with the Halbach array magnetic pole is analyzed. The magnetic field analysis method of the excitation source separation is proposed, and then, the transient analytical model of output electromagnetic force and the external circuit characteristic under displacement excitation is established. A modified particle swarm optimization algorithm is further adopted to optimize the structural parameters of TPMLM. By comparing with the finite element analysis, the correctness of the proposed analytical model and the optimization are verified. This work lays the theoretical foundation for extensive application of the regenerative suspension.


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## Body

## 1. Introduction

Vehicle body vibrates while running on the uneven road surface. This potential energy is mostly dissipated by the suspension system of 10–600 Watts [1, 2], accounting for about 30% of the power output energy. The recycling of this power will benefit the traditional fuel vehicles to reduce fuel consumption and improve the battery life cycle of electric vehicles. Due to the same travel direction as the suspension vibration and a higher power level and power density, the tubular permanent-magnet linear machine (TPMLM) is able to directly convert to electric power, which is convenient for storage and utilization. Therefore, compared to common ones like piezoelectric and electrostatic, the TPMLM has more application prospects in developing regenerated suspension, and it is also widely used in wave energy, road/bridge vibration energy regeneration, and so on. [3].The TPMLM-based regenerative suspension system requires not only to maintain the suspension performance but also to ensure high energy-feeding efficiency. It is necessary to optimize the structural parameters of the TPMLM. Scholars have carried out a lot of research studies and achieved some results. Zuo et al. [4] designed a four-phase linear generator. The finite element analysis (FEA) was used to analyze the magnetic field and assist in the design optimization. A simplified model was derived to qualitatively characterize the waveforms and regenerate power of the harvester at various vibration amplitude, frequencies, equilibrium positions, and structure parameters. The regenerative shock absorber will be able to harvest 16–64 W power. Asadi et al. [5, 6] proposed a hybrid damper combining TPMLM with hydraulic structure. The theoretical model and FEA were utilized to optimize the structural parameters. Damping and regenerative characteristics were tested by the prototype experiment, and the influence of the change of some structural parameters on the performance of the damper was revealed. Jiang et al. [7] made improvements in the structure of TPMLM. The simplified model was then established to optimize the thickness of the permanent magnet and the ratio of the pole pitch with the maximum air-gap magnetic flux. Characteristics of speed versus power under constant velocity excitation are simulated. Tang et al. [8] focused on the structural characteristics of TPMLM, such as the radial thickness of the coil. The FEA was used to optimize the regenerated power density and damping force. And, the novel TPMLM with double-layer permanent-magnet array was proposed, of which the power density was improved 5.6 times than the predesigned prototype. Liu et al. [9] established a new energy-regenerative active suspension system, employing an actuator composed of a shock absorber and a DC motor. The results verified the suspension performance and energy-regenerative efficiency. Wang et al. [10] proposed a supercapacitor mode-switching control strategy for the regenerative and semiactive suspension system.Among the above research studies, the magnetic circuit analysis or FEA is mainly used to optimize the TPMLM structure with the targets of damping and regenerated ability, by scanning the single or multiple parameters. Nevertheless, as a solution for the parameter optimization, sweeping under the complex external excitation using FEA consumes a long calculation time. It is therefore difficult to achieve global optimization of structural parameters because of the inability to solve multiple-parameter optimization at the same time. Optimization with analytical model can reduce calculating time to solve the abovementioned problem. But, due to the discontinuous inner magnetic field distribution of the TPMLM, it is difficult to establish analytical model which has similar precision to the FEA model, especially in dynamic characteristic. Representative research is the analytical model introducing the Carter coefficient correction for a three-phase tubular modular permanent-magnet machine proposed by Wang et al. [11–13]. The model was introduced in detail on the open-circuit magnetic field distribution with a quasi-Halbach magnetized armature. In addition, the electromagnetic force and electromechanical conversion efficiency are optimized for several sets of structural parameters. The analytical model proposed by Wang mainly describes the performance of the motor under static and constant velocity excitation. However, for complex random excitation such as road surface, it is necessary to further establish the transient analytical model to obtain the dynamic and winding circuit characteristics.This paper, therefore, proposed an analytical method based on excitation source separation for a moving-coil TPMLM. The transient model of the electromagnetic force and winding circuit under universal external excitation was derived. Furthermore, particle swarm optimization (PSO) algorithm is easy to implement, especially does not require different objective functions and constraints. Thus, the global optimal solution can be obtained with a large probability. A modified dual adaptive PSO was used to optimize the structural parameters globally, taking regenerated power as the target function. The FEA of TPMLM was then employed to verify the correctness of the transient analytical model and the effectiveness of structural optimization.


## 2. Analytical Model

### 2.1. Structure of TPMLM

The Halbach magnetized single-phase nonslot permanent-magnet linear machine (TPMLM, tubular permanent-magnet linear machine) is adopted, as shown in Figure1. The TPMLM is divided into five regions (I–V) according to the material medium, namely, the direct-axis region, the winding region, the air-gap region, the permanent magnet region, the back iron region, to derive dynamic and electric model based on the magnetic field analysis. With the actual motor structure considered, the following assumptions are made to facilitate the analysis of the electromagnetic field:(1)
The axial length is sufficiently large relative to its radial length, and the axial direction can be made infinitely long when resolving magnetic field(2)
Linearization of the B-H curve of the motor magnetic mediumFigure 1
Halbach magnetized nonslot moving-coil cylindrical permanent-magnet linear machine structure. Region I, direct-axis region; region II, winding region; region III, air-gap region; region IV, permanent magnet region; region V, back iron region.
(a)
(b)


### 2.2. Magnetic Vector Potential

The electromagnetic force-displacement dynamics of the TPMLM and the transient model of the winding voltage-displacement circuit based on magnetic field analysis are established. The key here lies in solving the magnetic field equation in the TPMLM, especially in winding region II. Based on Maxwell equations and substituting the magnetic medium constitutive equation, the vector potential differential equation is derived:(1)∇×1μ0μr∇×A=J+∇×Hc,where A represents the magnetic vector potential. B is the magnetic induction, which can be expressed by the magnetic vector potential B=∇×A under the Coulomb specification constraint. J represents the conduction current vector. Hc represents the magnetic medium coercive force vector. In the cylindrical coordinates, the magnetic vector potential A (r, θ, z) can be regarded only as the direction component of Aθ (r, z) [8] since the internal magnetic field of TPMLM is axisymmetric. Then, equation (1) is transformed into the following:(2)−1μ0μr∂2∂z2Aθ+∂∂r1r∂∂rrAθθ→=J+∇×Hcθ.Considering the magnetic medium characteristics of each region and expanding the winding conduction current density vector and the permanent magnet coercive force vector in the form of Fourier series, the magnetic vector potential equations in each region are derived;(3)∂2∂z2Aθi+∂∂r1r∂∂rrAθi=0,Regioni=I,III,V,∂2∂z2AθII+∂∂r1r∂∂rrAθII=Js∑n=1∞Qnsinmnz−x,Region II,∂2∂z2AθIV+∂∂r1r∂∂rrAθIV=∑n=1∞Pncosknz+τp4,Region IV,where Js represents θ direction component of the winding current density. Qn and Pn represent the series coefficient of Fourier series expansion of the winding current density and the permanent magnet coercive force (refer to the appendix). mn=kn=2n−1π/τp, where τp represents the pole pitch of the permanent magnet and x represents the displacement along the positive direction of the z-axis of the motor mover portion.The vector potential equations have a uniform homogeneous form with different nonhomogeneous terms in different regions. For the homogeneous part of the vector potential equation, the separation variable method is used to transform the original Laplace equation to the first-order modified Bessel equation and the second-order differential equation. The homogeneous solution is their universal solution product. Moreover, since magnetic field of TPMLM is produced by both the conduction currentJ and the coercive force HcIV of the permanent magnet, the homogeneous solution of the magnetic flux solution is as follows:(4)Aθir,z=Aθi1r,z+Aθi2r,z=∑nain1I1kinr+bin1K1kinr⋅cin1coskinz+din1+∑nain2I1minr+bin2K1minr⋅cin2cosminz+din2,Regioni=I,II,III,IV,V,where Aθi1 represents the homogeneous solution of the magnetic field equation generated by the conduction current and Aθi2 represents the homogeneous solution of the magnetic field equation generated by the coercive force of the permanent magnet. I1 is the solution of the first-order modified Bessel equation of the first kind. K1 is the solution of the first-order modified Bessel equation of the second kind.Firstly, the radial vector potential equation is simplified by the Fourier series. The variation of constants formula is further introduced to solve the radial equation in form of homogeneous Bessel equation. And then, special solutions of the nonhomogeneous vector potential equation for regions II and IV are derived:(5)AθII∗r,z,x=Js∑n=1∞G1mnrI1mnr+G2mnrK1mnr⋅sinmnz−x,AθIV∗r,z=∑n=1∞E1knrI1knr+E2knrK1knr⋅cosknz+τp4.Amongst,E1, E2, G1, and G2 are the coefficients of the nonhomogeneous Bessel function (refer to the appendix).Based on the general solution of the vector potential equation, the magnetic field boundary condition at the interface of the magnetic medium is further substituted, including the continuous condition of the normal condition of the magnetic induction intensity and the tangential condition of the magnetic field strength.(6)n→⋅B1−B2=0,n→×H1−H2=0,where n→ denotes the normal vector of the interface of the magnetic medium. B1/B2 and H1/H2 denote the magnetic induction intensity and magnetic field strength in the magnetic medium on both sides of the interface, respectively. For the motor to solve the region, the outer boundary has a vector potential at the outer boundary of zero, namely, Aθr=R0,r=Rb=0. By substituting in the above boundary conditions, the vector potential solutions of each region are obtained:(7)Aθir,z,x=∑n=1∞ain1I1knr+bin1K1knr⋅cosknz+τp4+∑n=1∞ain2I1mnr+bin2K1mnr⋅sinmnz−x,Regioni=I,III,V,AθIIr,z,x=∑n=1∞aIIn1I1knr+bIIn1K1knr⋅cosknz+τp4+∑n=1∞JsG1mnrI1mnr+JsG2mnrK1mnr+aIIn2I1mnr+bIIn2K1mnr⋅sinmnz−x,AθIVr,z,x=∑n=1∞E1mnrI1mnr+E2mnrK1mnr+aIVn1I1knr+bIVn1K1knr⋅cosknz+τp4+∑n=1∞aIVn2I1mnr+bIVn2K1mnr⋅sinmnz−x.The solution coefficients of Bessel function are as follows, and for the definition ofAn1, An2, Bn1, and Bn2, refer to the appendix:(8)An1aIn1bIn1aIIn1bIIn1aIIIn1bIIIn1aIVn1bIVn1aVn1bVn1T=Bn1,An2aIn2bIn2aIIn2bIIn2aIIIn2bIIIn2aIVn2bIVn2aVn2bVn2T=JsBn2.


### 2.3. Thrust Force and Winding Circuit

Based on the above analytical solution of the internal magnetic field, the thrust force and winding equation can be derived directly. Since the electromagnetic force of the nonslot linear motor is mainly generated by the armature reaction and the edge force generated by the asymmetry of the magnetic field is negligible compared to the ampere force, the thrust force of the TPMLM mover is derived as follows:(9)Fz=∫RegionIIJ×Bdvz=−∫RegionIIJsBrIIdv,where BrII represents the radial component of magnetic induction in region II; BrII = −dAθII/dz. Considering only the pure resistive load RL connected to the winding end, the winding circuit is expressed as follows:(10)ddtΨsxt+ddtΨjsxt+RDC+RL⋅isxt=0,where RDC represents the winding DC resistance; RDC=4mNρcRs0+RsNw2/KcRs−Rs0τp. ρc represents the winding wire conductivity. Kc represents full slot ratio. mN represents the winding slot amount. Nw represents the turns in the winding. is represents the winding current. iL is load current, iL (x) = −is (x). Ψs represents the winding flux linkage. Ψjs represents the winding current flux linkage.The volume integral of the winding magnetic induction can convert to surface integral inr-z plane by Stokes–Cartan theorem. Besides, due to the trigonometric characteristics of the axial integration of the vector potential, the expressions of the electromagnetic force and the flux linkage integral are simplified as follows:(11)Ψsxt=∑n=1∞H1ncosknxt+3τp4,Ψjsxt=isxt∑n=1∞H2n,Fzxt=isxt∑n=1∞H3nsinknxt+3τp4.The simplified series coefficients are as follows:(12)H1n=mNNwSw2⋅−1n+1kn∫Rs0Rs2πraIIn1I1knr+bIIn1K1knrdr,H2n=mNNwSw22mn∫Rs0Rs2πrG1mnrI1mnr+G2mnrK1mnr+aIIn2I1mnr+bIIn2K1mnrdr,H3n=−knH1n,where Sw represents the cross-sectional area of the winding slot.


### 2.4. Model Verification

A set of TPMLM structural parameters is selected, namely, motor dimensionsR0 = 4 mm, Rs0 = 8 mm, Rs = 16 mm, Rm = 17 mm, Rmb = 36 mm, and Rb = 40 mm. Relative permeability of each region are μrI = 800, μrII = 1, μrIII = 1, μrIV = 1.02, and μrV = 800. Pole pitch and residual magnetism of the permanent magnet are τp = 33 mm and Brem = 1.41 T, respectively. At the same time, the TPMLM FEM is established in the FEA software, to verify the proposed analytical model. According to Figure 1, the model is composed of iron core in direct-axis, winding coil, air-gap, permanent magnet, and back iron. The parameters of winding are mN = 6, Nw = 100, and Kc = 0.9. The boundary condition of solved region is balloon boundary. For the exterior area of iron core and back iron, the boundary condition is vectorpotential boundary. The motionsetup is moving along the direction of z-axis. The solver time is set as 0 to 5 s with the step of 0.001 s. Figure 2 shows the comparison between the FEA and the analytical analysis of the magnetic field in the winding region (r = 12 mm) along the z-axis, when the current density is zero.Figure 2
The FEA and analysis results of winding magnetic field. (a) Axial distribution of magnetic vector potential. (b) Axial distribution of magnetic induction.
(a)
(b)The results indicate that the curve of analytical magnetic induction is nearly consistent with that of FEA. Note, the vector potential has a not-too-large offset at the edge, which is because the number of permanent magnet arrays is limited. The comparison verifies the correctness and accuracy of the proposed internal vector potential analysis method.The axial damping force and the load voltage of the TPMLM whenRL = RDC are further carried out, under harmonic excitation x(t) = Am sin(2πft), where Am = 25 mm and f = 1.5 Hz, 15 Hz(the first and second resonant frequency of vehicle suspension is around 1.5 Hz and 15 Hz [14]). The two outputs of TPMLM, namely, axial damping force and load voltage, are selected as comparison data. They also represent mechanical and electrical properties, respectively. Figure 3 shows the comparison of FEA and the analytical result. Due to the finite length of the axial length of the iron and iron core and a limited number of permanent magnet arrays, the analytical damping force is somewhat different from the FEA, but the overall trend and the numerical values are basically consistent. Most of all, the analytical calculation process takes far less time than FEA.Figure 3
Comparison of FEA and analytical results. (a) Axial output damping force. (b) Load voltage (-1 denotes 1.5 Hz and -2 denotes 15 Hz).
(a)
(b)
(c)
(d)


## 2.1. Structure of TPMLM

The Halbach magnetized single-phase nonslot permanent-magnet linear machine (TPMLM, tubular permanent-magnet linear machine) is adopted, as shown in Figure1. The TPMLM is divided into five regions (I–V) according to the material medium, namely, the direct-axis region, the winding region, the air-gap region, the permanent magnet region, the back iron region, to derive dynamic and electric model based on the magnetic field analysis. With the actual motor structure considered, the following assumptions are made to facilitate the analysis of the electromagnetic field:(1)
The axial length is sufficiently large relative to its radial length, and the axial direction can be made infinitely long when resolving magnetic field(2)
Linearization of the B-H curve of the motor magnetic mediumFigure 1
Halbach magnetized nonslot moving-coil cylindrical permanent-magnet linear machine structure. Region I, direct-axis region; region II, winding region; region III, air-gap region; region IV, permanent magnet region; region V, back iron region.
(a)
(b)


## 2.2. Magnetic Vector Potential

The electromagnetic force-displacement dynamics of the TPMLM and the transient model of the winding voltage-displacement circuit based on magnetic field analysis are established. The key here lies in solving the magnetic field equation in the TPMLM, especially in winding region II. Based on Maxwell equations and substituting the magnetic medium constitutive equation, the vector potential differential equation is derived:(1)∇×1μ0μr∇×A=J+∇×Hc,where A represents the magnetic vector potential. B is the magnetic induction, which can be expressed by the magnetic vector potential B=∇×A under the Coulomb specification constraint. J represents the conduction current vector. Hc represents the magnetic medium coercive force vector. In the cylindrical coordinates, the magnetic vector potential A (r, θ, z) can be regarded only as the direction component of Aθ (r, z) [8] since the internal magnetic field of TPMLM is axisymmetric. Then, equation (1) is transformed into the following:(2)−1μ0μr∂2∂z2Aθ+∂∂r1r∂∂rrAθθ→=J+∇×Hcθ.Considering the magnetic medium characteristics of each region and expanding the winding conduction current density vector and the permanent magnet coercive force vector in the form of Fourier series, the magnetic vector potential equations in each region are derived;(3)∂2∂z2Aθi+∂∂r1r∂∂rrAθi=0,Regioni=I,III,V,∂2∂z2AθII+∂∂r1r∂∂rrAθII=Js∑n=1∞Qnsinmnz−x,Region II,∂2∂z2AθIV+∂∂r1r∂∂rrAθIV=∑n=1∞Pncosknz+τp4,Region IV,where Js represents θ direction component of the winding current density. Qn and Pn represent the series coefficient of Fourier series expansion of the winding current density and the permanent magnet coercive force (refer to the appendix). mn=kn=2n−1π/τp, where τp represents the pole pitch of the permanent magnet and x represents the displacement along the positive direction of the z-axis of the motor mover portion.The vector potential equations have a uniform homogeneous form with different nonhomogeneous terms in different regions. For the homogeneous part of the vector potential equation, the separation variable method is used to transform the original Laplace equation to the first-order modified Bessel equation and the second-order differential equation. The homogeneous solution is their universal solution product. Moreover, since magnetic field of TPMLM is produced by both the conduction currentJ and the coercive force HcIV of the permanent magnet, the homogeneous solution of the magnetic flux solution is as follows:(4)Aθir,z=Aθi1r,z+Aθi2r,z=∑nain1I1kinr+bin1K1kinr⋅cin1coskinz+din1+∑nain2I1minr+bin2K1minr⋅cin2cosminz+din2,Regioni=I,II,III,IV,V,where Aθi1 represents the homogeneous solution of the magnetic field equation generated by the conduction current and Aθi2 represents the homogeneous solution of the magnetic field equation generated by the coercive force of the permanent magnet. I1 is the solution of the first-order modified Bessel equation of the first kind. K1 is the solution of the first-order modified Bessel equation of the second kind.Firstly, the radial vector potential equation is simplified by the Fourier series. The variation of constants formula is further introduced to solve the radial equation in form of homogeneous Bessel equation. And then, special solutions of the nonhomogeneous vector potential equation for regions II and IV are derived:(5)AθII∗r,z,x=Js∑n=1∞G1mnrI1mnr+G2mnrK1mnr⋅sinmnz−x,AθIV∗r,z=∑n=1∞E1knrI1knr+E2knrK1knr⋅cosknz+τp4.Amongst,E1, E2, G1, and G2 are the coefficients of the nonhomogeneous Bessel function (refer to the appendix).Based on the general solution of the vector potential equation, the magnetic field boundary condition at the interface of the magnetic medium is further substituted, including the continuous condition of the normal condition of the magnetic induction intensity and the tangential condition of the magnetic field strength.(6)n→⋅B1−B2=0,n→×H1−H2=0,where n→ denotes the normal vector of the interface of the magnetic medium. B1/B2 and H1/H2 denote the magnetic induction intensity and magnetic field strength in the magnetic medium on both sides of the interface, respectively. For the motor to solve the region, the outer boundary has a vector potential at the outer boundary of zero, namely, Aθr=R0,r=Rb=0. By substituting in the above boundary conditions, the vector potential solutions of each region are obtained:(7)Aθir,z,x=∑n=1∞ain1I1knr+bin1K1knr⋅cosknz+τp4+∑n=1∞ain2I1mnr+bin2K1mnr⋅sinmnz−x,Regioni=I,III,V,AθIIr,z,x=∑n=1∞aIIn1I1knr+bIIn1K1knr⋅cosknz+τp4+∑n=1∞JsG1mnrI1mnr+JsG2mnrK1mnr+aIIn2I1mnr+bIIn2K1mnr⋅sinmnz−x,AθIVr,z,x=∑n=1∞E1mnrI1mnr+E2mnrK1mnr+aIVn1I1knr+bIVn1K1knr⋅cosknz+τp4+∑n=1∞aIVn2I1mnr+bIVn2K1mnr⋅sinmnz−x.The solution coefficients of Bessel function are as follows, and for the definition ofAn1, An2, Bn1, and Bn2, refer to the appendix:(8)An1aIn1bIn1aIIn1bIIn1aIIIn1bIIIn1aIVn1bIVn1aVn1bVn1T=Bn1,An2aIn2bIn2aIIn2bIIn2aIIIn2bIIIn2aIVn2bIVn2aVn2bVn2T=JsBn2.


## 2.3. Thrust Force and Winding Circuit

Based on the above analytical solution of the internal magnetic field, the thrust force and winding equation can be derived directly. Since the electromagnetic force of the nonslot linear motor is mainly generated by the armature reaction and the edge force generated by the asymmetry of the magnetic field is negligible compared to the ampere force, the thrust force of the TPMLM mover is derived as follows:(9)Fz=∫RegionIIJ×Bdvz=−∫RegionIIJsBrIIdv,where BrII represents the radial component of magnetic induction in region II; BrII = −dAθII/dz. Considering only the pure resistive load RL connected to the winding end, the winding circuit is expressed as follows:(10)ddtΨsxt+ddtΨjsxt+RDC+RL⋅isxt=0,where RDC represents the winding DC resistance; RDC=4mNρcRs0+RsNw2/KcRs−Rs0τp. ρc represents the winding wire conductivity. Kc represents full slot ratio. mN represents the winding slot amount. Nw represents the turns in the winding. is represents the winding current. iL is load current, iL (x) = −is (x). Ψs represents the winding flux linkage. Ψjs represents the winding current flux linkage.The volume integral of the winding magnetic induction can convert to surface integral inr-z plane by Stokes–Cartan theorem. Besides, due to the trigonometric characteristics of the axial integration of the vector potential, the expressions of the electromagnetic force and the flux linkage integral are simplified as follows:(11)Ψsxt=∑n=1∞H1ncosknxt+3τp4,Ψjsxt=isxt∑n=1∞H2n,Fzxt=isxt∑n=1∞H3nsinknxt+3τp4.The simplified series coefficients are as follows:(12)H1n=mNNwSw2⋅−1n+1kn∫Rs0Rs2πraIIn1I1knr+bIIn1K1knrdr,H2n=mNNwSw22mn∫Rs0Rs2πrG1mnrI1mnr+G2mnrK1mnr+aIIn2I1mnr+bIIn2K1mnrdr,H3n=−knH1n,where Sw represents the cross-sectional area of the winding slot.


## 2.4. Model Verification

A set of TPMLM structural parameters is selected, namely, motor dimensionsR0 = 4 mm, Rs0 = 8 mm, Rs = 16 mm, Rm = 17 mm, Rmb = 36 mm, and Rb = 40 mm. Relative permeability of each region are μrI = 800, μrII = 1, μrIII = 1, μrIV = 1.02, and μrV = 800. Pole pitch and residual magnetism of the permanent magnet are τp = 33 mm and Brem = 1.41 T, respectively. At the same time, the TPMLM FEM is established in the FEA software, to verify the proposed analytical model. According to Figure 1, the model is composed of iron core in direct-axis, winding coil, air-gap, permanent magnet, and back iron. The parameters of winding are mN = 6, Nw = 100, and Kc = 0.9. The boundary condition of solved region is balloon boundary. For the exterior area of iron core and back iron, the boundary condition is vectorpotential boundary. The motionsetup is moving along the direction of z-axis. The solver time is set as 0 to 5 s with the step of 0.001 s. Figure 2 shows the comparison between the FEA and the analytical analysis of the magnetic field in the winding region (r = 12 mm) along the z-axis, when the current density is zero.Figure 2
The FEA and analysis results of winding magnetic field. (a) Axial distribution of magnetic vector potential. (b) Axial distribution of magnetic induction.
(a)
(b)The results indicate that the curve of analytical magnetic induction is nearly consistent with that of FEA. Note, the vector potential has a not-too-large offset at the edge, which is because the number of permanent magnet arrays is limited. The comparison verifies the correctness and accuracy of the proposed internal vector potential analysis method.The axial damping force and the load voltage of the TPMLM whenRL = RDC are further carried out, under harmonic excitation x(t) = Am sin(2πft), where Am = 25 mm and f = 1.5 Hz, 15 Hz(the first and second resonant frequency of vehicle suspension is around 1.5 Hz and 15 Hz [14]). The two outputs of TPMLM, namely, axial damping force and load voltage, are selected as comparison data. They also represent mechanical and electrical properties, respectively. Figure 3 shows the comparison of FEA and the analytical result. Due to the finite length of the axial length of the iron and iron core and a limited number of permanent magnet arrays, the analytical damping force is somewhat different from the FEA, but the overall trend and the numerical values are basically consistent. Most of all, the analytical calculation process takes far less time than FEA.Figure 3
Comparison of FEA and analytical results. (a) Axial output damping force. (b) Load voltage (-1 denotes 1.5 Hz and -2 denotes 15 Hz).
(a)
(b)
(c)
(d)


## 3. Structural Parameter Optimization

The size of the TPMLM is limited by the processing technique, installing environmental conditions and other limitations. It is necessary to optimize parameters of the TPMLM, with target of the maximum power point. The winding equation is deformed as follows, considering characteristic of general loadRX {R, L}:(13)ddtΨsxt+Ls⋅ddtisxt+RDC⋅isxt+RXis,is′=0.The winding inductanceLs of the nonslot TPMLM is extremely small, and the electromotive force by armature reaction is much smaller than the voltage of the internal resistance of the winding. Hence, it can be considered that the maximum output power Pmax is obtained when RX = RDC. The motor structure dimensions such as air gap thickness, iron/core thickness, permanent magnet thickness, and maximum outer diameter are constrained, and the optimization model of the structural size {RX} = {R0, Rs0, Rs, Rm, Rmb, Rb} is proposed as follows, whose objective function is output power:(14)minfRX=−PmaxRX,s.t.gjRX≥0,j=1,…,m,Lb≤RX≤Ub,where Pmax (RX) represents the maximum average power under the structure size of {RX} and Pmax=∫t0t0+TRL⋅iL2dt/T indicates m groups of inequality linear and nonlinear constraints. Lb and Ub represent the lower and upper boundaries of the structural size, respectively. The feasible solution region composed of the constraint condition is defined as f.Generally, the optimal size of the motor will appear around the boundary. Therefore, the proposed dual fitness function PSO algorithm is used to solve the optimization problem of the TPMLM, to regenerate maximum output power under constraint. The two fitness functions of each particle are(16)fitnessi=fRX,i=1,2,…,n,voilationi=∑j=1mmingjRX,0,where i denotes the i-th particle, n denotes the population size of the particle group, fitness(i) denotes the particle fitness of the objective function, and voilation(i) denotes the particle fitness of the conditional constraint. The comparison criterions between each particle are as follows:(1)
Both particlesa and b are in the feasible region, and the particle with smaller fitness(i) is better.(2)
Both particlesa and b are not in the feasible region, and the particle with smaller voilation(i) is better.(3)
The particlea is in the feasible region, while the particle b is not. If the voilation(b) < ε, the particle with smaller fitness(i) is better, otherwise the particle a is better.The comparison of two fitness functions allows the particles to quickly approach the feasible domain boundary and obtain a feasible solution that satisfies the constraints. At the same time, a certain infeasible solution ratio can be ensured by controlling the tolerant boundary, thus making the optimization be more quick and stable.Figure4(a) shows the PSO calculation process. The population size n is set to 80, the tolerance boundary ε = 0.02 mm, the infeasible solution ratio p is 0.15, and the excitation is a harmonic with a amplitude of 25 mm and a frequency of 1.5 Hz. Waves, the particle swarm converges to the optimal solution after 30 iterations. Figure 4(b) shows the optimal instantaneous output power. Table 1 is comparison of performance with structural parameters before and after optimization. The results demonstrate the feasibility of the TPMLM maximum power optimization model and the applicability of the established TPMLM dynamic and electric transient models.Figure 4
Optimization results. (a) Optimization process. (b) Instantaneous power under optimal parameters.
(a)
(b)Table 1
Performance comparison before and after optimization.
Structure parameters {RX} (mm)
Average power (W)
RMS of damping force (N)
1.5 Hz
15 Hz
1.5 Hz
15 Hz
Before optimization
{4, 8, 16, 17, 36, 40}
11.80
1.86
172.75
67.68
After optimization
{4, 10.9, 15.9, 16.9, 36, 40}
13.36
2.59
195.54
74.36


## 4. Conclusions

In this paper, a Halbach magnetized single-phase nonslot moving-coil TPMLM is designed. The magnetic analysis method which separates excitation is proposed, and then, transient analysis model of the damping force and winding circuit is established under external excitation. The transient model has the similar accuracy to FEA. Based on the analytical model, the improved dual-adaptive particle swarm optimization algorithm is utilized to obtain the optimal parameter of the TPMLM maximum power point operation with a short calculation time, which further indicates that the proposed TPMLM analytical model is applicable for optimization. The proposed analytical model can also be applied to the dynamic analysis of combined vibration damping system.



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*Source: 5635047-2019-12-02.xml*