# Low Cross-Polarization Gaussian Tapered Post-Wall Slotline Antenna for Short Pulse Applications

Authors: Hongxin Zhao; Yufu Li; Xiaoxing Yin
Journal: International Journal of Antennas and Propagation
 (2017)

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## Abstract

A Gaussian tapered slot antenna based on post-wall structured slotline for improvement of cross-polarization for ultra-wideband applications is proposed and experimentally demonstrated. The antenna is composed of two pairs of Gaussian tapered slotline which have the same structure printed on both sides of the PCB, two metallic via arrays positioned along the slot edges, and two terminal resistors. The metallic via arrays are used to reduce the characteristic impedance of the conventional slotline which form a post-wall slotline and thus can be fed by a coaxial connector directly. More importantly, the balanced symmetrical post-wall structure ensures low cross-polarization levels of the antenna. The Gaussian tapered edges and the terminal resistors diminish reflected signal and thus can enlarge the bandwidth significantly. Good agreements between the simulated and the measured results have been observed. Results show that the proposed antenna exhibits a −10 dB impedance bandwidth from 1.5 GHz to 20 GHz, a maximum realized gain of 12 dBi, and the broadside cross-polarization level is averaged about −32 dB in the lower frequency band and −25 dB in the higher frequency band with a maximum value of −22 dB in the whole working frequency band.


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## Body

## 1. Introduction

With the rapid development of the ultra-wideband and short pulse applications in UWB communication systems and ground penetrating radar (GPR), ultra-wideband antennas, such as TEM horn, log-periodical, helical, and tapered slot antennas (TSA), have been widely studied in recent years. Tapered slot antenna (TSA) is widely used in modern wireless communication systems because of its wideband property, moderate gain, low cost, simple fabrication, planar structure, and good time domain performance [1–5]. TSAs can be categorized into end-fire travelling wave antenna, in which the electromagnetic energy is guided and radiated along the edge of slot [6]. The most concerned in the design of TSAs is the feeding and radiation structure. As the characteristic impedance of the slotline is quite high, a transition from a 50 Ohm coaxial adapter or a microstrip feeding network to the slotline usually shows unsatisfactory performance over the wide bandwidth of the TSA or has complicated structures [7–10]. In order to overcome the bandwidth limitation of feeding structure for the conventional TSAs, antipodal TSA and its various forms with fins printed on opposite sides of the substrate were presented by many researchers in the past. Compared to the traditional TSAs, antipodal TSAs can be fed easily with microstrip lines and SMA connectors, but it is not suitable in large array applications and its cross-polarization levels is quite high [11–17]. For the radiation structure, a plethora of tapered profiles, such as the common exponential profile and linear profile, have been reported to design TSAs. However, the sudden discontinuity at the antenna terminal still produces large reflection, which lays severe constraints on the antenna bandwidth [18, 19].In this letter, a novel ultra-wideband Gaussian tapered post-wall slotline antenna is proposed. The post-wall slotline [20, 21] is featured by low characteristic impedance and it can be fed by a coaxial connector directly, which is beneficial for diminishing the reflection signal. The smooth Gaussian tapered slot edge and the terminal resistors are favorable for enlarging the bandwidth. Due to its bilateral and symmetrical structure, loading resistor can be easily mounted and cross-polarization level can be highly suppressed compared to the design in [17]. It is demonstrated by the simulated results and the measured results that the proposed antenna is featured by broad bandwidth, low cross-polarization levels, moderate gain, and suitability for short pulse applications.


## 2. Antenna Geometry and Design

The geometry of the proposed Gaussian tapered post-wall slotline antenna is shown in Figure1. The antenna is printed on a substrate of Rogers 4003C, with size of l×w, a thickness of 0.813 mm, relative permittivity of 3.55, and loss tangent of 0.0027. The post-wall slotline of the antenna is composed of a bilateral slotline and two arrays of metallic vias which are aligned along the slot edges. The fins of the bilateral slotline on top and bottom surface of the substrate are with the same structure and are connected by the metallic vias. The vias in each array are placed uniformly and compactly to form the conductive post-wall. Therefore, the capacitance per unit length of the post-wall slotline is higher than that of a common slotline, which effectuates low characteristic impedance and enables the direct feeding by a coaxial connector.Figure 1
Configuration of proposed Gaussian tapered post-wall slotline antenna.The edges of the post-wall form a rhombus-like shape and taper in accordance with a Gaussian function. Denoting the turn of the rhombus as pointA and positioning the original point of the coordinate system under point A, the Gaussian tapered profile can be expressed as follows:(1)xz=m·exp-4πzτ12,for-l1≤z≤0m·exp-4πzτ22,for0≤z≤l2,where m determines the maximum of the Gaussian function, τ1 and τ2 indicate the width of the Gaussian profiles, and l1 and l2 denote the length of the diverging region from the feeding point to point A and the length of the converging region from point A to the end of the slotline, respectively. The derivative of the Gaussian function at point A is designed to be zero, which indicates a smooth transition from the diverging region to the converging region. Two terminal resistors, with value of R, are loaded to connect the two converging fins on top and bottom surfaces of the substrate, respectively. The smooth Gaussian tapered profile and the terminating resistors corporately enlarge the bandwidth.The proposed Gaussian tapered post-wall slotline antenna has been simulated and optimized using CST MWS. The value of the loaded resistor and key parameters for the Gaussian tapered profile influence the reflected signal a lot. Figure2 shows, respectively, S11 with different values of R,  τ1.Figure 2
Effect ofR and τ1. (a) Simulated S11 and realized gain with different value of R, (b) simulated total efficiency with different value of R, and (c) simulated S11 with different value of τ1.
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(c)Figure3 shows, respectively, the photograph of the top side and bottom side of the proposed antenna. The final results with the optimized parameters for the proposed antenna are listed below.Figure 3
Photos of the proposed antenna. (a) Top side and (b) bottom side.l=112 mm, w=53.4 mm, l1=84 mm, l2=23 mm, R=200 Ohm, τ1=99.2, and  τ2=42.4.
(a)
(b)


## 3. Simulated and Experimental Results

The proposed Gaussian tapered post-wall slotline antenna has been measured using an Agilent vector network analyzer N5230A in anechoic chamber. A Gaussian pulse with a −10 dB impedance bandwidth from 0 to 20 GHz is used to excite the proposed antenna. The simulated and measured reflection coefficients of the proposed antenna are shown in Figure4(a).Figure 4
Simulated and measured port parameters. (a) Simulated and measured reflection coefficients and (b) input and reflected signals.
(a)
(b)Time domain characterization is an attractive description method for short pulse antenna performance. To illustrate the short pulse performance of the proposed antenna, port signals in time domain derived from the measured scattering parameters are depicted in Figure4(b) along with simulated results. The Gaussian pulse with a −10 dB bandwidth from DC to 20 GHz is utilized as the stimulus signal and is expressed as(2)Gt=exp-4πt-t02τ2,where t0 equals 0.08885 ns and τ is 0.086 ns. The spectrum of the Gaussian pulse is denoted by G(f). The Gaussian pulse shown in (2) is used to calculate the pulse waveforms along with the measured scattering parameters. The measured reflected pulse signal b11(t) is derived as follows: (3)b11t=IFFTEOGf·S11-mf,where S11-m(f) represents the measured scattering parameters of the fabricated antenna and E/O represents the even symmetry operation of the magnitude spectrum and the odd symmetry operation of the phase spectrum.A good agreement has been observed between the simulated and the measured results. Both of the results show thatS11 is lower than −10 dB from about 1.5 GHz to 20 GHz, which indicates the ultra-wideband property of the proposed antenna. Figure 4(b) shows the input signal and the reflected signal observed at the feed port in the simulation. It is seen that the peak value of the reflected signal is lower than 0.1 and the trailing pulse after 1.25 ns is quite small, which also indicates the good impedance matching of the antenna.Simulated efficiency of the presented antenna at different frequencies is shown in Figure5; it can be concluded that the total efficiency is more than 70% in the whole working frequency band. Figure 6(a) depicts the simulated and measured realized gain in the main radiation direction of the proposed antenna. It can be found that the measured gain agrees quite well with the simulated results in most of the working frequency band, and the gain is larger than about 3 dBi from 4 GHz with a peak value of 12 dBi at 12.5 GHz. Figure 6(b) gives the comparison between the simulated and the measured cross-polarization levels in the main radiation direction of the proposed antenna. The simulated result shows that the cross-polarization level of the proposed antenna increases from lower frequency band to higher frequency band and is lower than −30 dB across the concerned frequency band. The measured result is larger than the simulated result, but it can be observed that the measured cross-polarization level is lower than −22 dB across the whole frequency band.Figure 5
Simulated efficiency.Figure 6
Gain and cross-polarization level. (a) Realized gain in main radiation direction and (b) cross-polarization levels in main radiation direction.
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(b)The simulated and measured radiation patterns in theE-plane andH-plane are shown in Figure 7. Considering the broad bandwidth of the proposed antenna, the patterns at 6 GHz and 14 GHz are given to characterize the radiation performance. As shown in Figure 7, the simulated and measured radiation patterns in copolarization agree quite well. The proposed antenna has directional radiation patterns and the main direction is along the z-axis. The measured cross-polarization levels at 6 GHz and at 14 GHz are both lower than −20 dB inE-plane and are lower than about −15 dB inH-plane.Figure 7
Simulated and measured radiation patterns. (a) Patterns inE-plane at 6 GHz, (b) patterns inH-plane at 6 GHz, (c) patterns inE-plane at 14 GHz, and (d) patterns inH-plane at 14 GHz.
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(b)
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(d)To obtain the transmission performance, two identical proposed antennas were placed 1.3 meters apart along the main radiation direction in the anechoic chamber and the transmission coefficientsS21(f) under the copolarization and the cross-polarization conditions were measured by using vector network analyzer. Figure 8 gives the measured transmission signals b21(f) of the two identical antennas positioned in copolarization and in cross-polarization, respectively.Figure 8
The transmission of short pulse signals between two antennas.


## 4. Conclusion

An ultra-wideband rhombus-like Gaussian tapered post-wall slotline antenna is proposed. The rhombus-like post-wall slotline presents low characteristic impedance and is fed by a coaxial connector directly and enables low cross-polarization levels of the antenna. The Gaussian tapered edges and the terminal resistors diminish reflected signal and enlarge the bandwidth significantly. Good agreements between the simulated and the measured results have been observed. Results show that the proposed antenna exhibits −10 dB impedance bandwidth from 1.5 GHz to 20 GHz, a maximum realized gain of 12 dBi, and the broadside cross-polarization levels lower than −22 dB in the whole working frequency band.



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*Source: 4852709-2017-07-31.xml*