# Design of High Efficiency Illumination for LED Lighting

Authors: Yong-Nong Chang; Hung-Liang Cheng; Chih-Ming Kuo
Journal: International Journal of Photoenergy
 (2013)

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## Abstract

A high efficiency illumination for LED street lighting is proposed. For energy saving, this paper uses Class-E resonant inverter as main electric circuit to improve efficiency. In addition, single dimming control has the best efficiency, simplest control scheme and lowest circuit cost among other types of dimming techniques. Multiple serial-connected transformers used to drive the LED strings as they can provide galvanic isolation and have the advantage of good current distribution against device difference. Finally, a prototype circuit for driving 112 W LEDs in total was built and tested to verify the theoretical analysis.


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## Body

## 1. Introduction

Green energy and high efficiency equipment have been developed rapidly to mitigate to global warming problem. In order to improve the efficiency of lighting equipments, light emitting diode (LED) has been paid attention and adopted as the light source. LED has the highest lighting efficiency among other lighting equipments. Furthermore, it possesses longer life cycle, faster dynamic response, smaller device volume and higher color rendering index. LED lighting equipments are widely used for automobiles [1–4], indoor lightings [5], outdoor lights [6, 7], and street lamps recently. LED lighting equipments are look upon as the main lighting equipment in the future. In order to replace traditional lighting equipments, LED lighting equipments of high output power are developing rapidly in recent years. Performance of LED lighting equipment has been paid attention to, such as efficiency of LED drivers, device reliability, and dimming features. In this paper, multiple serial-connected transformers are used to overcome the problems mentioned above.In order to drive the multiple serial-connected transformers, an inverter is required. Class-E serial resonant inverter will be used in this paper as main electric circuit. Class-E resonant inverter can achieve higher efficiency than Class-D resonant inverter [8, 9]. In order to lower the usage of electricity for lightings during daytime, dimming features are seen as a way to save energy of lighting equipments. Conventional ways to achieve dimming feature is to use linear current-regulator to control LED lighting equipments individually [10]. Another way is to use PWM controller to achieve dimming control [11, 12], but PWM controller without current limitation function causes the shrink of life cycle of LED. Dimming switches of both ways do not have the ability of soft switching, which involves switching losses during dimming control. In this paper, integral-cycle control is used to achieve ZCS function of dimming switches, minimizing the power losses during dimming control.There are several different control schemes to achieve same output power of an LED lighting equipment. This paper proposes three types of different dimming controls for multiple serial-connected transformers. Three types of dimming controls include synchronism dimming control, sequential dimming control, and single dimming control. The efficiency and control scheme are both compared in this paper to find out the best dimming control scheme.


## 2. Topology and Analysis of Proposed Circuit

To improve the efficiency of street lighting, Class-E resonant inverter is used in this paper. Class-E resonant inverter possesses higher efficiency than other types of inverter. The class-E resonant inverter in this paper will be operated in close to optimum mode to ensure ZVS function of the main switch at all time. Figure1 shows the proposed circuit in this paper. Figure 2 shows the theoretical optimum waveforms of operating modes of class-E resonant inverter; it can be categorized into 4 modes as shown in Figure 3; the modes are described as follows.Figure 1
Proposed circuit in this paper.Figure 2
Theoretical optimum waveforms of Class-E resonant inverter.Figure 3
Operating modes of proposed circuit.


### 2.1. Mode I:t0<t<t1

When switch S1 turns off, Mode I starts. As the switch of the resonant inverter turns off, currentIIN-Ir is in positive cycle. The current is flowing through the parallel capacitor C1 and, voltage on C1 is raised from zero. Mode I ends when the resonant current passes through zero and the circuit enters the next mode.


### 2.2. Mode II:t1<t<t2

Mode II starts when the resonant current enters positive cycle and ends when current ofC1, Ic1 passes through zero point and then the circuit enters Mode III.


### 2.3. Mode III:t2<t<t3

Mode III starts when the currentIIN-Ir passes through zero and enters negative cycle. The main switch of class-E resonant inverter remains off. The current IIN-Ir enters negative cycle and so is the current of capacitor C1, Ic1. The voltage on the parallel capacitor C1 begins to discharge. This mode ends when current IIN-Ir passes through zero and enters the positive cycle.


### 2.4. Mode IV:t3<t<t4

Mode IV starts after currentIIN-Ir enters positive cycle. Parallel capacitor C1 is completely discharged and the main switch turns on. Since the voltage applied on the parallel capacitor drops to zero and so is the voltage applied on the main switch. Therefore, the main switch of Class-E resonant inverter achieves zero-voltage switching (ZVS) function and reduces switching losses. This mode ends when the resonant current becomes negative and the circuit enters Mode I of the next high frequency cycle.Reactance changes to resonant tank during dimming control might result in current variation. Current variation might result in malfunction of LED street lamp, which influences the safety of drivers, and it is not acceptable. Class-E resonant inverter must be well designed to prevent unacceptable current variation. Therefore, characteristics of proposed circuit are analyzed as follows.To simplify the analysis, the circuit is simplified as in Figure4. As shown in Figure 5, in order to simplify the parameters design, the loads are equivalent to the primary side of transformers Rp. The value of the input inductor will influence the ripple of input current which can be expressed as in (1). The value of DC input current can be estimated by (2). With a high load quality factor, almost all the harmonic contents and Dc components will be filtered by the resonant tank. Only the fundamental current at the switching frequency will be present in the load circuit. Therefore, the load resonant circuit can be analyzed using the fundamental component approximation. The fundamental voltage Vc1 applied on parallel capacitor C1 can be estimated by (3)
(1)ΔL1,pp=VINL1DT,⟹L1=VINΔiL,PPDT,(2)IIN=PVIN,(3)Vc1≈22×VINπ.Figure 4
Simplified circuit.Figure 5
Equivalent power resistanceRp.During dimming control, the resonant current is impossible to be kept unchanged, and determination of the maximum loading current is essential. The variation of LED current is proportional to the variation of resonant current, and the resonant current is dominated byZLC and RT. The minimum resonant current Irmin will occur at full load; minimum resonant current Irmin can be expressed as in (4), where n is the number of LED lighting sets. When LED lighting sets are shorted during dimming control, the resonant current will rise to the maximum. The maximum resonant current Irmax occurs when only one equivalent resistance of LED set participates in the resonant tank. Irmax can be expressed as in (5). With Tx being defined as ratio of ZLC and RP as expressed by (6), the resonant current ratio of Irmin and Irmax, K can be expressed as in (7)
(4)Irmin=Vc1(nRP)2+(ZLC)2,(5)Irmax=Vc1(RP)2+(ZLC)2,(6)ZLC=|TXRP|,(7)K≡IrminIrmax=(1+TX2)(n2+TX2),
where K is the current ratio of Irmin and Irmax.As shown in (8), according to Kirchhoff’s voltage law (KVL), voltage of the resonant tank is equal to the sum of the voltage applied on resonant components and loads, and, wherein, the RT can be found by (9). Since the ratio of reactance ZLC to Rp has been found, voltage applied on single transformer VRP with full load can be calculated by (10)
(8)(Vc1)2=(VRT)2+(VZLC)2,(9)RT=n×RP,(10)VRP=Vc12n2+Tx2.The specifications of LED lighting sets are given in Table1. The operating voltage of LED lighting set at rate output, Vlamp, will be estimated by (11), where the ILEDmin can be estimated by (12)
(11)Vlamp=VLED+ILEDmin·RLED,(12)ILEDmin=ILED×K.Table 1
Specifications of proposed circuit.
Input voltage,VIN
140 V
Current ratio,K
0.7
Turn ratio,a
0.30
Turn ratio of dimming circuit
0.125
Switching frequency,fs
50 kHz
Resonant frequency,fr
40 kHz
Maximum loading current of LED,ILED
350 mA
Operating voltage of LED,VLED
78.8 V
Total output power,Po
112 W
Value of output capacitor,Con
330μFWith the voltages of both sides of transformers being found out, turn ratioNp/Ns can be estimated by (13)
(13)a≡NPNS=π×VRP22×VLamp,
where a is the turn ratio in this paper.Moreover, the resonant current during full load can be referred from the secondary side of transformer to the primary side; the RMS value of full load resonant currentIrmin can be estimated by (14)
(14)Irmin=π×ILEDmin22×a.Since all the components are ideal, there will be no power losses in transformers, and the input power is equal to the output power; therefore, the input power of primary side can be estimated by (15)
(15)PRP=ILEDmin×VLamp.With the input powerPRp and the resonant current of primary side Irmin, the equivalent power resistance can be estimated by (16)
(16)RP≡PRP(Irmin)2=8×a2×VLampπ2×ILEDmin,
where Rp is the equivalent power resistance in the primary side of transformers.Since the value ofC1 influences whether the main switch of class-E resonant inverter has the capability of zero-voltage switching (ZVS) function or not, analysis of parallel capacitor C1 is critical in this research. If the resonant current is defined as (17), the output power can be expressed as in (18). If RMS value of resonant current is expressed as in (19), the peak value of resonant current can be expressed as in (20). The current of parallel capacitor C1, Ic1, is expressed as in (21). The instantaneous voltage of parallel capacitor C1, Vc1(t), is expressed as in (22). Vc1(t3) will drop to zero at time instant t3 as expressed by (23). Besides, Vc1(t3) can be expressed as in (24). Therefore, the angle, Φ, by which the resonant voltage leads the resonant current can be found by deducing (24). The mean voltage of C1, Vc1av will be equal to the input voltage VIN as in (25). The mean voltage of C1, Vc1av, can be expressed as in (26). Therefore, the value of C1 can be rewritten as in (27), and the value can be found by deriving (27)
(17)Ir=Iosin(ωt-Φ),(18)P=Ir2×RT,(19)Ir(rms)=4×ILEDmin×VLampRT,(20)Io(peak)=8×ILEDmin×VLampRT,(21)ic1(t)=IIN-Iosin(ωt-Φ),(22)Vc1(t)=1C1∫t0t[IIN-Iosin(ωt-Φ)]dt=1C1[IIN×t+Ioωcos(ωt-Φ)-IoωcosΦ],(23)Vc1(t3)=0,(24)Vc1(t3)=1C1∫tot3[IDC-Iosin(ωt-Φ)]dt=1C1[(1-D)T×IIN+Ioωcos(2Dπ+Φ)-IoωcosΦ],(25)Vc1av=VIN,(26)Vc1av=1T∫t0(1-D)TVc1(t)dt=1C1{(1-D)2T2IIN-(1-D)T2πcosΦ×Io+T4π2Io[sinΦ-sin(2Dπ+Φ)](1-D)2T2},(27)C1=1VIN{(1-D)2T2IIN-(1-D)T2πcosΦ×Io+T4π2Io[sinΦ-sin(2Dπ+Φ)](1-D)2T2IIN}.Using the parameters of resonant frequency of resonant tankfr and switching frequency fs defined in Table 1, the reactance ZLC defined as in (28) and resonant components Cr and Lr can be solved by deducing simultaneous (28), where K is the resonant current ratio of Irmin and Irmax(28)ZLC=ωsLr-1ωsCr,ωr=2πfr=1LrCr.


## 2.1. Mode I:t0<t<t1

When switch S1 turns off, Mode I starts. As the switch of the resonant inverter turns off, currentIIN-Ir is in positive cycle. The current is flowing through the parallel capacitor C1 and, voltage on C1 is raised from zero. Mode I ends when the resonant current passes through zero and the circuit enters the next mode.


## 2.2. Mode II:t1<t<t2

Mode II starts when the resonant current enters positive cycle and ends when current ofC1, Ic1 passes through zero point and then the circuit enters Mode III.


## 2.3. Mode III:t2<t<t3

Mode III starts when the currentIIN-Ir passes through zero and enters negative cycle. The main switch of class-E resonant inverter remains off. The current IIN-Ir enters negative cycle and so is the current of capacitor C1, Ic1. The voltage on the parallel capacitor C1 begins to discharge. This mode ends when current IIN-Ir passes through zero and enters the positive cycle.


## 2.4. Mode IV:t3<t<t4

Mode IV starts after currentIIN-Ir enters positive cycle. Parallel capacitor C1 is completely discharged and the main switch turns on. Since the voltage applied on the parallel capacitor drops to zero and so is the voltage applied on the main switch. Therefore, the main switch of Class-E resonant inverter achieves zero-voltage switching (ZVS) function and reduces switching losses. This mode ends when the resonant current becomes negative and the circuit enters Mode I of the next high frequency cycle.Reactance changes to resonant tank during dimming control might result in current variation. Current variation might result in malfunction of LED street lamp, which influences the safety of drivers, and it is not acceptable. Class-E resonant inverter must be well designed to prevent unacceptable current variation. Therefore, characteristics of proposed circuit are analyzed as follows.To simplify the analysis, the circuit is simplified as in Figure4. As shown in Figure 5, in order to simplify the parameters design, the loads are equivalent to the primary side of transformers Rp. The value of the input inductor will influence the ripple of input current which can be expressed as in (1). The value of DC input current can be estimated by (2). With a high load quality factor, almost all the harmonic contents and Dc components will be filtered by the resonant tank. Only the fundamental current at the switching frequency will be present in the load circuit. Therefore, the load resonant circuit can be analyzed using the fundamental component approximation. The fundamental voltage Vc1 applied on parallel capacitor C1 can be estimated by (3)
(1)ΔL1,pp=VINL1DT,⟹L1=VINΔiL,PPDT,(2)IIN=PVIN,(3)Vc1≈22×VINπ.Figure 4
Simplified circuit.Figure 5
Equivalent power resistanceRp.During dimming control, the resonant current is impossible to be kept unchanged, and determination of the maximum loading current is essential. The variation of LED current is proportional to the variation of resonant current, and the resonant current is dominated byZLC and RT. The minimum resonant current Irmin will occur at full load; minimum resonant current Irmin can be expressed as in (4), where n is the number of LED lighting sets. When LED lighting sets are shorted during dimming control, the resonant current will rise to the maximum. The maximum resonant current Irmax occurs when only one equivalent resistance of LED set participates in the resonant tank. Irmax can be expressed as in (5). With Tx being defined as ratio of ZLC and RP as expressed by (6), the resonant current ratio of Irmin and Irmax, K can be expressed as in (7)
(4)Irmin=Vc1(nRP)2+(ZLC)2,(5)Irmax=Vc1(RP)2+(ZLC)2,(6)ZLC=|TXRP|,(7)K≡IrminIrmax=(1+TX2)(n2+TX2),
where K is the current ratio of Irmin and Irmax.As shown in (8), according to Kirchhoff’s voltage law (KVL), voltage of the resonant tank is equal to the sum of the voltage applied on resonant components and loads, and, wherein, the RT can be found by (9). Since the ratio of reactance ZLC to Rp has been found, voltage applied on single transformer VRP with full load can be calculated by (10)
(8)(Vc1)2=(VRT)2+(VZLC)2,(9)RT=n×RP,(10)VRP=Vc12n2+Tx2.The specifications of LED lighting sets are given in Table1. The operating voltage of LED lighting set at rate output, Vlamp, will be estimated by (11), where the ILEDmin can be estimated by (12)
(11)Vlamp=VLED+ILEDmin·RLED,(12)ILEDmin=ILED×K.Table 1
Specifications of proposed circuit.
Input voltage,VIN
140 V
Current ratio,K
0.7
Turn ratio,a
0.30
Turn ratio of dimming circuit
0.125
Switching frequency,fs
50 kHz
Resonant frequency,fr
40 kHz
Maximum loading current of LED,ILED
350 mA
Operating voltage of LED,VLED
78.8 V
Total output power,Po
112 W
Value of output capacitor,Con
330μFWith the voltages of both sides of transformers being found out, turn ratioNp/Ns can be estimated by (13)
(13)a≡NPNS=π×VRP22×VLamp,
where a is the turn ratio in this paper.Moreover, the resonant current during full load can be referred from the secondary side of transformer to the primary side; the RMS value of full load resonant currentIrmin can be estimated by (14)
(14)Irmin=π×ILEDmin22×a.Since all the components are ideal, there will be no power losses in transformers, and the input power is equal to the output power; therefore, the input power of primary side can be estimated by (15)
(15)PRP=ILEDmin×VLamp.With the input powerPRp and the resonant current of primary side Irmin, the equivalent power resistance can be estimated by (16)
(16)RP≡PRP(Irmin)2=8×a2×VLampπ2×ILEDmin,
where Rp is the equivalent power resistance in the primary side of transformers.Since the value ofC1 influences whether the main switch of class-E resonant inverter has the capability of zero-voltage switching (ZVS) function or not, analysis of parallel capacitor C1 is critical in this research. If the resonant current is defined as (17), the output power can be expressed as in (18). If RMS value of resonant current is expressed as in (19), the peak value of resonant current can be expressed as in (20). The current of parallel capacitor C1, Ic1, is expressed as in (21). The instantaneous voltage of parallel capacitor C1, Vc1(t), is expressed as in (22). Vc1(t3) will drop to zero at time instant t3 as expressed by (23). Besides, Vc1(t3) can be expressed as in (24). Therefore, the angle, Φ, by which the resonant voltage leads the resonant current can be found by deducing (24). The mean voltage of C1, Vc1av will be equal to the input voltage VIN as in (25). The mean voltage of C1, Vc1av, can be expressed as in (26). Therefore, the value of C1 can be rewritten as in (27), and the value can be found by deriving (27)
(17)Ir=Iosin(ωt-Φ),(18)P=Ir2×RT,(19)Ir(rms)=4×ILEDmin×VLampRT,(20)Io(peak)=8×ILEDmin×VLampRT,(21)ic1(t)=IIN-Iosin(ωt-Φ),(22)Vc1(t)=1C1∫t0t[IIN-Iosin(ωt-Φ)]dt=1C1[IIN×t+Ioωcos(ωt-Φ)-IoωcosΦ],(23)Vc1(t3)=0,(24)Vc1(t3)=1C1∫tot3[IDC-Iosin(ωt-Φ)]dt=1C1[(1-D)T×IIN+Ioωcos(2Dπ+Φ)-IoωcosΦ],(25)Vc1av=VIN,(26)Vc1av=1T∫t0(1-D)TVc1(t)dt=1C1{(1-D)2T2IIN-(1-D)T2πcosΦ×Io+T4π2Io[sinΦ-sin(2Dπ+Φ)](1-D)2T2},(27)C1=1VIN{(1-D)2T2IIN-(1-D)T2πcosΦ×Io+T4π2Io[sinΦ-sin(2Dπ+Φ)](1-D)2T2IIN}.Using the parameters of resonant frequency of resonant tankfr and switching frequency fs defined in Table 1, the reactance ZLC defined as in (28) and resonant components Cr and Lr can be solved by deducing simultaneous (28), where K is the resonant current ratio of Irmin and Irmax(28)ZLC=ωsLr-1ωsCr,ωr=2πfr=1LrCr.


## 3. Experimental Results

In this paper, a high efficiency street lighting is proposed. Table1 shows the specification of the proposed circuit, following the design procedures in the previous section. Parameters can be deduced as in Table 2. Figure 6 shows the waveforms of the Class-E resonant inverter during full load using the parameters listed in Table 2. Experimental waveforms show that the experimental results are in good consistency with the theoretical prediction.Table 2
Parameters deduced from design procedures.
Input inductor,L1
10 mH
Voltage apply onC1, Vc1
126 V
Magnification of resistance,TX
3.66
Equivalent power resistance,RT
118Ω
Voltage apply on a single transformer,VRP
23.24 V
Minimum resonant current,Irmin
0.9 A
Minimum loading current of LEDs,ILED min
280 mA
Value of parallel capacitor,C1
20.5 nF
Value of resonant capacitor,Cr
49 nF
Value of resonant inductor,Lr
321μHFigure 6
Experimental waveforms of Class-E resonant inverter.Figures7 and 8 show the waveforms which indicate that the main switch is able to achieve ZVS function in both full load and single load. Figure 7 shows the voltage waveforms of Vgs and Vc1 during single load and Figure 8 shows the voltage waveforms of Vgs and Vc1 during full load. Resonant current will flow through the body diode of the main switch before it turns on. It can be clearly seen that the main switch of the Class-E resonant inverter has achieved ZVS function in both full load and single load as demanded.Figure 7
Waveforms of ZVS function of the main switch of Class-E resonant inverter during single load.Figure 8
Waveforms of ZVS function of the main switch of Class-E resonant inverter during full load.


## 4. Discussions of Different Types of Dimming Control

With integral-cycle control being used in this paper to implement the dimmer design, wide range and precise dimming control can be achieved. During dimming control, reactance changes will occur. There are several ways to achieve same output effect with different dimming control techniques. The relationship between different dimming techniques and reactance changes will be discussed in this section. The frequency of dimming signalVgs-dim is 500 Hz and switching frequency of the Class-E resonant inverter is 50 kHz. Dimming range is made possible from 0.25% to 100%. Since street lamps are operated at rate output, generally, they do not require wide range of dimming control. The dimming control of 35% to 100% rated power is proposed in this paper. Output capacitors with great value are used in this paper to limit the effect of current variation occurrence during dimming control.


### 4.1. Synchronism Dimming Control

The first way to control the LED lighting set is to control all the lighting sets simultaneously, while the LED lighting sets are able to produce the same amount of output power. But in this way, the reactance will change at any time, leading to a huge reactance change to the whole system during dimming control.Figure9 shows 60% rated power; Figure 10 shows 35% rated power. Theoretically, the mean value of loading current ILEDn under 85% output of dimming control is about 238 mA, while it is 168 mA under 60% output of dimming control, 98 mA under 35% output of dimming control, and 56 mA under 20% output of dimming control.Figure 9
60% output of synchronism dimming control.Figure 10
35% output of synchronism dimming control.


### 4.2. Sequential Dimming Control

To avoid reactance changes at any time and leading huge reactance to whole system, sequential dimming control is proposed. LED lighting sets are separated into 2 groups, with 1 ms delay of each group. The reactance changes of each LED lamp can be equally shared in different periods, which lower the reactance changes comparing to synchronism dimming control. Figure11 shows 60% output of dimming control; Figure 12 shows 35% output of dimming control. In these ways, four sets of integral control circuits must be required, and control scheme is complicated as well.Figure 11
60% output of sequential dimming control.Figure 12
35% output of sequential dimming control.


### 4.3. Single Dimming Control

Last technique is single dimming control. Only one LED lighting set is in charge of detail dimming control while the rest of the LED lighting sets are kept either on or off. In this way, only one set needs the Integral-Cycle Control circuit, which can reduce the circuit cost and simplify the control scheme, the reactance change is the lowest as well.Figure13 shows 60% output of dimming control; Figure 14 shows 35% output of dimming control.Figure 13
60% output of single dimming control.Figure 14
35% output of single dimming control.Finally, we compare the efficiency of the three types of dimming controls, Figure15 shows the efficiency of the three types of dimming controls. Single dimming control has the best efficiency among the three types; it requires one integral-cycle control circuit only, reduces reactance changes during dimming control, and is a comparatively simplified dimming control scheme. Figure 16 shows the lumen curve of single dimming control from 35% to 100% output.Figure 15
Efficiency of three types of dimming controls.Figure 16
Lumen curve of single dimming control.


## 4.1. Synchronism Dimming Control

The first way to control the LED lighting set is to control all the lighting sets simultaneously, while the LED lighting sets are able to produce the same amount of output power. But in this way, the reactance will change at any time, leading to a huge reactance change to the whole system during dimming control.Figure9 shows 60% rated power; Figure 10 shows 35% rated power. Theoretically, the mean value of loading current ILEDn under 85% output of dimming control is about 238 mA, while it is 168 mA under 60% output of dimming control, 98 mA under 35% output of dimming control, and 56 mA under 20% output of dimming control.Figure 9
60% output of synchronism dimming control.Figure 10
35% output of synchronism dimming control.


## 4.2. Sequential Dimming Control

To avoid reactance changes at any time and leading huge reactance to whole system, sequential dimming control is proposed. LED lighting sets are separated into 2 groups, with 1 ms delay of each group. The reactance changes of each LED lamp can be equally shared in different periods, which lower the reactance changes comparing to synchronism dimming control. Figure11 shows 60% output of dimming control; Figure 12 shows 35% output of dimming control. In these ways, four sets of integral control circuits must be required, and control scheme is complicated as well.Figure 11
60% output of sequential dimming control.Figure 12
35% output of sequential dimming control.


## 4.3. Single Dimming Control

Last technique is single dimming control. Only one LED lighting set is in charge of detail dimming control while the rest of the LED lighting sets are kept either on or off. In this way, only one set needs the Integral-Cycle Control circuit, which can reduce the circuit cost and simplify the control scheme, the reactance change is the lowest as well.Figure13 shows 60% output of dimming control; Figure 14 shows 35% output of dimming control.Figure 13
60% output of single dimming control.Figure 14
35% output of single dimming control.Finally, we compare the efficiency of the three types of dimming controls, Figure15 shows the efficiency of the three types of dimming controls. Single dimming control has the best efficiency among the three types; it requires one integral-cycle control circuit only, reduces reactance changes during dimming control, and is a comparatively simplified dimming control scheme. Figure 16 shows the lumen curve of single dimming control from 35% to 100% output.Figure 15
Efficiency of three types of dimming controls.Figure 16
Lumen curve of single dimming control.


## 5. Conclusion

Via precise design of the Class-E resonant inverter, LED street lamps can prevent damage from current variation during dimming control. From experimental results, multiple serial-connected transformers have successfully solved the problems of power isolation and current uniformity. Single dimming control is the best way of achieving dimming feature. Not only did it reduce the reactance changes during dimming control, but it also achieves comparatively the highest efficiency as well, leading to curtailing circuit cost and simplifying the control scheme. Finally, an 112 W high efficiency illumination for LED street lighting is developed, and efficiency can maintain 94% and 10270 lm at rate output.



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*Source: 471384-2013-11-24.xml*