# Broadband Printed Cross-Dipole Element with Four Polarization Reconfigurations for Mobile Base Station Array Antenna Applications

Authors: Soon-Young Eom; Ic-Pyo Hong; Jong-Myeon Kim
Journal: International Journal of Antennas and Propagation
 (2011)

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## Abstract

This paper describes a broadband printed cross-dipole element with four polarization reconfigurations (BPCDE_PR). The BPCDE_PR can configure two linear and two circular polarizations in the operating band of 1.7–2.5 GHz. To implement the broadband polarization reconfigurations, switched network type broadband phase shifters are proposed and designed. The fabricated BPCDE_PR prototype with switched network including broadband phase shifters shows good electrical performances and the desired polarization reconfigurable functions in the operating band.


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## Body

## 1. Introduction

In wireless mobile communication systems, base stations or repeater antennas are essential for their role in making a wireless signal path connection with wireless terminals. In conventional technology, they are usually designed for single-mode operation that radiates mainly linear polarization. However, in the future, various wireless services will gradually converge to the use of a single wireless multimode terminal that can give multimode functions operating according to a selected service or frequency band. Fading will be dependent upon wireless service bands and surrounding environments and will cause a distortion or change of excited polarization. A switchable property in polarization or frequency can allow the user to access any existing network. In this regard, it is desirable that base stations or repeater antennas also provide multimode functions to reconfigure polarization and/or frequency.Numerous researchers have recently investigated polarization or frequency reconfigurable antennas [1–6] but most of the results showed narrow bandwidth characteristics. Practically, it is difficult to use such antenna schemes due to complicated switching circuits. In this paper, a new broadband printed cross-dipole (CDP) element with four polarization reconfigurations (BPCDE_PR) is proposed to improve the operating bandwidth. It is designed in the operating band of 1.7–2.5 GHz (about 40% in fractional bandwidth). The broadband feed network proposed in this paper to control polarization shows good electrical performances of over 50%. The BPCDE_PR proposed in this paper can control linear (+45°/−45°) polarizations or circular polarizations (LHCP/RHCP) in the operating band for PCS, WCDMA, WiBro, and WLAN (WiFi) services in South Korea. The proposed antenna can also be used as an array element in broadband base stations or repeater antennas, or broadband terminal antennas because of its broadband characteristics and polarization reconfigurability.


## 2. BPCDA_PR Design

The internal block diagram of the BPCDE_PR proposed in this paper is shown in Figure1. A broadband printed cross-dipole element is put on the top side of the BPCDE_PR, and a broadband feed network that can generate and control four different polarizations is attached on its bottom side.Figure 1
Internal block diagram of BPCDE_PR.In order to implement the broadband polarization antenna element proposed in this paper, a broadband antenna element and a broadband feed network for polarization reconfiguration (BFN_PR) are required as shown in Figure1. The antenna element is composed of two linear antennas that form an orthogonal structure and radiates two orthogonal linear components, Ex and Ey, into free space. Its two inputs are physically connected with two outputs of a feed network. To make the properly linear or circular polarizations mentioned above, two output signals from the feed network should be precisely controlled over the desired broadband [7].


### 2.1. Broadband Antenna Element

The broadband antenna element is composed of two printed dipole elements, and each printed dipole element is orthogonally crossed on the base ground plate. Each printed dipole element with a balun circuit is shown in Figure2, and the incident wave directly radiates in free space. The balun circuit in this element is used for transforming an unbalanced signal to a balanced signal and input impedance matching [8]. Although the I/O impedance transformation ratio of the integrated balun structure is not large, it can give a simple implementation and allows the designer to choose various optimal design parameters.Design parameters of each printed dipole element (TD=0.76mm, Wd=17.50mm, Ld=84.00mm, Hd=49.50mm, Wg=3.00mm, Ws=26.00mm, Hs=6.00mm, Wf=1.00mm, Lf11=22.30mm, Lf12=20.30mm, Lf2=15.50mm, Lf3=5.00mm).
(a)
Front and back-view of dipole 1(b)
Front and back view of dipole 2(c)
Top viewThe printed dipole element is realized on a RF35 board from the Taconic company with a dielectric permittivity of 3.5 and a thickness of 0.762 mm, and a conductor thickness of 0.035 mm. The design parameters of the printed dipole element were optimized using CST Microwave Studio (Ver. 5.1). The final design parameters are summarized in Figure2. The input feed line Lf1 has two different values (Lf11 and Lf12) with an offset of ±1 mm in order not to overlap in an orthogonal cross-section as shown in Figures 2(a) and 2(b).Antenna gain and radiation patterns can be changed significantly by placing the cross-dipole element into a cavity enclosure and changing the geometry of the enclosure. It is found that the presence of cavity enclosure limits the amount of radiation to the sides and back. Also, the cavity can provide the positive effect on antenna gain and radiation pattern [9]. Therefore, a metallic cavity ring structure is introduced in order to provide stable radiation patterns with a high gain characteristic over the operating band. The printed cross-dipole element is put at the center of the cavity ring with a diameter of 140 mm (≅0.98 λo), a height of 49.5 mm (≅0.35 λo), and a thickness of 1 mm.Figure3 shows the measured electrical performances of a printed cross-dipole element with and without the cavity ring over the operating band. As shown in Figure 3(a), the measured port return loss is less than −11.5 dB without the cavity ring and −9.3 dB with it. The isolation between the two ports shows more than 35 dB without the cavity ring and 32 dB with it. The radiation patterns of the printed cross-dipole element without the cavity ring, which are measured at 1.7 GHz, 2.1 GHz, and 2.5 GHz, show antenna gains at boresight of 9.1 dBi, 7.3 dBi, 5.8 dBi, respectively, shown in Figures 3(b)–3(d). A pit at 0 degree of the H-plane pattern at 2.5 GHz shown in Figure 3(d) is due to the finite ground plane with the size of 200 mm × 200 mm applied in the antenna prototype which corresponds to 2.35 λo at 2.5 GHz. The ground plane size and edges will have influence on the antenna properties, and the diffraction from the finite ground plane edges can cause main beam scalloping and can give a small effect on the directivity [10, 11]. On the other hand, radiation patterns of the printed cross-dipole element with the cavity ring show antenna gains at boresight of 9.4 dBi, 9.2 dBi, 10.2 dBi, respectively. The cross polarization performance is more than 21.2 dB within the 3 dB beamwidth and in the test frequencies irrespective of the usage of the cavity ring.Measured electrical performances of the printed cross-dipole element with or without the cavity ring.
(a)
Port return loss and isolation(b)
Radiation pattern at 1.7 GHz(c)
Radiation pattern at 2.1 GHz(d)
Radiation pattern at 2.5 GHzThese results reveal that the usage of the cavity ring provides radiation patterns of high quality and also a gain improvement of 1.9 dB and 4.4 dB at the middle and highest band, respectively.


### 2.2. Broadband Feed Network for Four Polarization Reconfigurations

As shown in Figure1, the broadband feed network for four polarization reconfigurations (BFN_PR) is composed of a two-stage Wilkinson power divider with equal power ratio, a broadband phase shifter (BPS) of 90°-bit, a BPS of 180°-bit, and a digital polarization control circuit including a DC stabilizing circuit. The block diagram of the two-stage Wilkinson power divider is shown in Figure 4, and design values were obtained under the conditions of f2/f1=1.5, and S11(max)=-35dB, S22, S33(max)=-49dB, I(min)=37dB [12], where f1 and f2 are the edge frequencies of the band S11, S22, and S33 represent the return loss at each port, and I represents the isolation between the output ports.Figure 4
Two-stage Wilkinson power divider.The block diagrams of broadband 90°/180° phase shifters are shown in Figure5. The phase shifters used in this paper were switched network types that were detailed in [13]. The 90° BPS structure of Figure 5(a) can achieve over octave bandwidths, and the 180° BPS structure of Figure 5(b) can operate in approximately a 50% fractional bandwidth. Each network is composed of two paths, Path 1 and Path 2, and a path is chosen by the simultaneous operation of two SPDT (Single Pole Double Throw) switches. SWM-2-50DR switches of mini-circuits are utilized in this design. Its insertion loss is about 1.5 dB, and the in-out isolation is more than 35 dB in the operating band. Path 2 has a more dispersive phase property than Path 1, and the phase slope can be controlled by the specific values of Zm to Zs. The design parameters of broadband 90°/180° phase shifter structures are determined by the design graph of Figure 6.Broadband 90°/180° phase shifter structures.
(a)
90° BPS structure(b)
180° BPS structureFigure 6
Design graph for 90°/180° BPS [13].The internal PCB and component layout of the prototype fabricated to verify the electrical performances of the BFN_PR is shown in Figure7. The BFN_PR circuit was also realized on an RF35 board from the Taconic company with a dielectric permittivity of 3.5 and a thickness of 0.508 mm, and a conductor thickness of 0.035 mm. Electrical design parameters of the BFN_PR are given in Figures 4 and 5.Figure 7
Fabricated BFN_PR prototype.Figure8 shows the measured electrical performances of the BFN_PR. The measured input and output return losses are less than −13.0 dB and −12.5 dB, respectively, in the operating band, and the measured insertion loss is less than −6.3 dB in the operating band. If the insertion losses of the two SPST switches assembled on each path of a switched network are excluded, the practical loss by the physical length and impedance mismatch is just about −3.3 dB. This means the BFN_PR itself has a very low loss or high efficiency. In addition, the relative phase shift error to the required phase shift is less than ±3.6° and +5.5° at 90° and 180° bit, respectively, in the operating band.Measured electrical performances of the BFN_PR prototype.
(a)
S11(b)
S22(c)
S21(d)
phase ofS21


## 2.1. Broadband Antenna Element

The broadband antenna element is composed of two printed dipole elements, and each printed dipole element is orthogonally crossed on the base ground plate. Each printed dipole element with a balun circuit is shown in Figure2, and the incident wave directly radiates in free space. The balun circuit in this element is used for transforming an unbalanced signal to a balanced signal and input impedance matching [8]. Although the I/O impedance transformation ratio of the integrated balun structure is not large, it can give a simple implementation and allows the designer to choose various optimal design parameters.Design parameters of each printed dipole element (TD=0.76mm, Wd=17.50mm, Ld=84.00mm, Hd=49.50mm, Wg=3.00mm, Ws=26.00mm, Hs=6.00mm, Wf=1.00mm, Lf11=22.30mm, Lf12=20.30mm, Lf2=15.50mm, Lf3=5.00mm).
(a)
Front and back-view of dipole 1(b)
Front and back view of dipole 2(c)
Top viewThe printed dipole element is realized on a RF35 board from the Taconic company with a dielectric permittivity of 3.5 and a thickness of 0.762 mm, and a conductor thickness of 0.035 mm. The design parameters of the printed dipole element were optimized using CST Microwave Studio (Ver. 5.1). The final design parameters are summarized in Figure2. The input feed line Lf1 has two different values (Lf11 and Lf12) with an offset of ±1 mm in order not to overlap in an orthogonal cross-section as shown in Figures 2(a) and 2(b).Antenna gain and radiation patterns can be changed significantly by placing the cross-dipole element into a cavity enclosure and changing the geometry of the enclosure. It is found that the presence of cavity enclosure limits the amount of radiation to the sides and back. Also, the cavity can provide the positive effect on antenna gain and radiation pattern [9]. Therefore, a metallic cavity ring structure is introduced in order to provide stable radiation patterns with a high gain characteristic over the operating band. The printed cross-dipole element is put at the center of the cavity ring with a diameter of 140 mm (≅0.98 λo), a height of 49.5 mm (≅0.35 λo), and a thickness of 1 mm.Figure3 shows the measured electrical performances of a printed cross-dipole element with and without the cavity ring over the operating band. As shown in Figure 3(a), the measured port return loss is less than −11.5 dB without the cavity ring and −9.3 dB with it. The isolation between the two ports shows more than 35 dB without the cavity ring and 32 dB with it. The radiation patterns of the printed cross-dipole element without the cavity ring, which are measured at 1.7 GHz, 2.1 GHz, and 2.5 GHz, show antenna gains at boresight of 9.1 dBi, 7.3 dBi, 5.8 dBi, respectively, shown in Figures 3(b)–3(d). A pit at 0 degree of the H-plane pattern at 2.5 GHz shown in Figure 3(d) is due to the finite ground plane with the size of 200 mm × 200 mm applied in the antenna prototype which corresponds to 2.35 λo at 2.5 GHz. The ground plane size and edges will have influence on the antenna properties, and the diffraction from the finite ground plane edges can cause main beam scalloping and can give a small effect on the directivity [10, 11]. On the other hand, radiation patterns of the printed cross-dipole element with the cavity ring show antenna gains at boresight of 9.4 dBi, 9.2 dBi, 10.2 dBi, respectively. The cross polarization performance is more than 21.2 dB within the 3 dB beamwidth and in the test frequencies irrespective of the usage of the cavity ring.Measured electrical performances of the printed cross-dipole element with or without the cavity ring.
(a)
Port return loss and isolation(b)
Radiation pattern at 1.7 GHz(c)
Radiation pattern at 2.1 GHz(d)
Radiation pattern at 2.5 GHzThese results reveal that the usage of the cavity ring provides radiation patterns of high quality and also a gain improvement of 1.9 dB and 4.4 dB at the middle and highest band, respectively.


## 2.2. Broadband Feed Network for Four Polarization Reconfigurations

As shown in Figure1, the broadband feed network for four polarization reconfigurations (BFN_PR) is composed of a two-stage Wilkinson power divider with equal power ratio, a broadband phase shifter (BPS) of 90°-bit, a BPS of 180°-bit, and a digital polarization control circuit including a DC stabilizing circuit. The block diagram of the two-stage Wilkinson power divider is shown in Figure 4, and design values were obtained under the conditions of f2/f1=1.5, and S11(max)=-35dB, S22, S33(max)=-49dB, I(min)=37dB [12], where f1 and f2 are the edge frequencies of the band S11, S22, and S33 represent the return loss at each port, and I represents the isolation between the output ports.Figure 4
Two-stage Wilkinson power divider.The block diagrams of broadband 90°/180° phase shifters are shown in Figure5. The phase shifters used in this paper were switched network types that were detailed in [13]. The 90° BPS structure of Figure 5(a) can achieve over octave bandwidths, and the 180° BPS structure of Figure 5(b) can operate in approximately a 50% fractional bandwidth. Each network is composed of two paths, Path 1 and Path 2, and a path is chosen by the simultaneous operation of two SPDT (Single Pole Double Throw) switches. SWM-2-50DR switches of mini-circuits are utilized in this design. Its insertion loss is about 1.5 dB, and the in-out isolation is more than 35 dB in the operating band. Path 2 has a more dispersive phase property than Path 1, and the phase slope can be controlled by the specific values of Zm to Zs. The design parameters of broadband 90°/180° phase shifter structures are determined by the design graph of Figure 6.Broadband 90°/180° phase shifter structures.
(a)
90° BPS structure(b)
180° BPS structureFigure 6
Design graph for 90°/180° BPS [13].The internal PCB and component layout of the prototype fabricated to verify the electrical performances of the BFN_PR is shown in Figure7. The BFN_PR circuit was also realized on an RF35 board from the Taconic company with a dielectric permittivity of 3.5 and a thickness of 0.508 mm, and a conductor thickness of 0.035 mm. Electrical design parameters of the BFN_PR are given in Figures 4 and 5.Figure 7
Fabricated BFN_PR prototype.Figure8 shows the measured electrical performances of the BFN_PR. The measured input and output return losses are less than −13.0 dB and −12.5 dB, respectively, in the operating band, and the measured insertion loss is less than −6.3 dB in the operating band. If the insertion losses of the two SPST switches assembled on each path of a switched network are excluded, the practical loss by the physical length and impedance mismatch is just about −3.3 dB. This means the BFN_PR itself has a very low loss or high efficiency. In addition, the relative phase shift error to the required phase shift is less than ±3.6° and +5.5° at 90° and 180° bit, respectively, in the operating band.Measured electrical performances of the BFN_PR prototype.
(a)
S11(b)
S22(c)
S21(d)
phase ofS21


## 3. Experimental Results

The BPCDE_PR prototype fabricated for testing four polarization reconfigurations is shown in Figure9. The printed cross-dipole element was assembled on a base plate of 150 mm × 150 mm to reflect the electromagnetic wave radiated from it to the boresight direction. Two outputs of the BFN_PR were connected with the cross-dipole element through two short coaxial lines with the same electrical length.Photos of the fabricated BPCDE_PR prototype.
(a)
Front side(b)
Back sidePolarization reconfigurations of the BPCDE_PR can be obtained by the digital polarization control circuit which makes relative phase differences of 0°, 180°, 90°, and −90°, respectively, at two outputs of the BFN_PR. The control paths for polarization reconfigurations in Figure7 are given in Table 1. Path 2 and Path 3 are the reference paths at each switched network.Table 1
Control paths for polarization reconfigurations.
PolarizationRelative phase differencesPath 1Path 2Path 3Path 4+45° linear0°OFFONONOFF−45° linear180°ONOFFONOFFLHCP90°ONOFFOFFONRHCP−90°OFFONOFFONThe input return losses measured according to the polarization reconfigurations are shown in Figure10, and the performances are less than −10.5 dB for four different polarizations in the operating band.Figure 10
Measured return loss of the BPCDE_PR prototype versus polarization reconfigurations.The radiation patterns and axial ratios measured according to the polarization reconfigurations are shown in Figures11 and 12, respectively. The gain and axial ratio performances of the BCDE_PR by test frequencies and different polarizations are summarized in Table 2.Table 2
Gain and axial ratio performances of BPCDE_PR.
FrequencyPolarizationGain (dBi)Max. axial ratio (dB) at 3 dB beamwidth1.7 GHz+45° linear7.19−20.75−45° linear7.19−24.54LHCP6.801.58RHCP6.661.612.1 GHz+45° linear7.17−19.97−45° linear7.07−17.02LHCP7.471.96RHCP7.052.232.5 GHz+45° linear7.55−17.89−45° linear7.38−19.30LHCP7.052.08RHCP6.692.07Measured radiation patterns of the BPCDE_PR prototype.
(a)
+45° linear pol.(b)
−45° linear pol.(c)
LHCP(d)
RHCPMeasured axial ratios of the BPCDE_PR prototype.
(a)
+45° linear pol.(b)
−45° linear pol.(c)
LHCP(d)
RHCPTable2 shows that the measured gain of the BPCDE_PR is the range of 6.66–7.47 dBi (with a 0.81 dB gain difference). The measured antenna gains are lower than the antenna gains of Figures 3(b)–3(d) due to the insertion loss of two SPST switches used in the feed network as shown in Figure 8(c). If SPDT switches with low loss are used or active amplifiers with low noise or high power between the printed cross-dipole elements and the polarization control circuit are used, the antenna gains would be increased and antenna efficiencies would be also increased.The measured axial ratios of +45° and −45° linear polarizations within 3 dB beamwidth are less than −17.89 dB and −17.02 dB in the operating band, respectively. The axial ratios of the LHCP and RHCP are less than 2.08 dB and 2.23 dB, respectively. The axial ratio performances could be improved a little in the next design by fine-matching the BFN_PR with the broadband printed cross-dipole element.The measured gain performances versus the frequency of the BPCDE_PR prototype are shown in Figure13. The frequency gain responses of +45° and −45° linear polarizations are within the range of 6.75–8.48 dBi and 6.50–8.93 dBi for the operating band, respectively, and also the frequency gain responses of the LHCP and RHCP are within the range of 6.35–9.08 dBi and 6.16–8.99 dBi, respectively. The cross polarization performances at the bore sight are more than 19.86 dB, 18.29 dB and 18.64 dB, 17.89 dB, respectively, for the operating band.Measured gain performances versus frequency of the BPCDE_PR prototype.
(a)
Linear(b)
Circular


## 4. Conclusions

A broadband printed cross-dipole element and feed network were designed and fabricated to test four polarization reconfigurations composed of two linear and two circular polarizations in the operating band of 1.7–2.5 GHz. To implement the broadband polarization reconfigurations, broadband 90°/180° phase shifters of switched network types were designed and showed good electrical performances. The fabricated BPCDE_PR showed appropriate polarization reconfigurations and good electrical performances in the operating band of about 40%. The proposed antenna in this paper can be used as an array element in broadband base stations and repeater antennas or as a broadband terminal antenna because of its broadband characteristics and polarization reconfigurability.



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*Source: 427015-2011-06-30.xml*