# High Gain and High Efficient Stacked Antenna Array with Integrated Horn for 60 GHz Communication Systems

Authors: Hamsakutty Vettikalladi; Waleed Tariq Sethi; Majeed A. Alkanhal
Journal: International Journal of Antennas and Propagation
 (2014)

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## Abstract

In order to achieve wide bandwidth and high gain, we propose a stacked antenna structure having a microstrip aperture coupled feeding technique with a mounted Horn integrated on it. With optimized parameters, the single antenna element at a center frequency of 60 GHz, exhibits a wide impedance bandwidth of about 10.58% (58.9–65.25 GHz) with a gain and efficiency of 11.78 dB and 88%, respectively. For improving the gain, we designed a 2 × 2 and 4 × 4 arrays with a corporate feed network. The side lobe levels were minimized and the back radiations were reduced by making use of a reflector atλ
/
4 distance from the corporate feed network. The 2
×
2 array structure resulted in improved gain of 15.3 dB with efficiency of 83%, while the 4
×
4 array structure provided further gain improvement of 18.07 dB with 68.3% efficiency. The proposed design is modelled in CST Microwave Studio. The results are verified using HFSS, which are found to be in good agreement.


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## Body

## 1. Introduction

Soon after the development of 60 GHz standard that provides a 7 GHz license-free bandwidth worldwide, its popularity became evident at millimeter waves spectrum due to its usage in high data-rate wireless communications at gigabit per second [1, 2]. The huge amount of bandwidth availability attracted the researchers for its use in many terrestrial and space applications. In this modern era of consumer electronic gadgets, even telephony and cable operated devices in offices and homes are trending towards wireless technology. The demand for higher data rate of these multimedia technologies can be resolved with 60 GHz standard as being a viable candidate.In any radio communication or wireless systems, antenna plays a vital part [3–5]. Since its development, the microstrip planar antennas [6] have gained popularity in telecommunication and radar applications due to its lightweight and low profile configurations. Microstrip patch antennas are among the best candidates for implementing in microwave and millimeter waves (MMW) frequency and they are good candidates for arrays as well. There are several reports devoted to the design and explanation of such antennas using arrays [7–12]. However, the traditional microstrip antennas have reached their maximum usability as they offer narrow bandwidth (3%) and low gain. Researchers investigated new methods and came up with coupling techniques to improve impedance bandwidth. The proposed solution by Pozar [13] is provided with wide bandwidth and high gain as compared to conventional microstrip antennas. The aperture coupling method enabled the patch antennas to be easily integrated into arrays, with active circuits, to minimize spurious radiations from the feed, and to introduce more freedom of substrates selections. Many techniques have been explained in the literature for improving bandwidth and gain at MMW [14–20].In this paper, a stacked microstrip antenna utilizing aperture-coupled technique with a mounted Horn on FR-4 substrate is presented, at a center frequency of 60 GHz. By employing this technique, a wide impedance bandwidth of about 10.58% (58.9–65.25 GHz) is achieved with high gain and efficiency. The gain and efficiency of the single element antenna are further increased by presenting a corporate fed network of 2 × 2 and 4 × 4 arrays. The 2 × 2 array structure resulted in improved gain of 15.3 dB with efficiency of 83%. While the 4 × 4 array structure provided further gain improvement of 18.07 dB with 68.3% efficiency. This paper is an extended work of our previous results [21], which had limited bandwidth. Comparing with previous results [21], the proposed single element antenna’s simulation results show improvement in terms of bandwidth and gain at millimeter waves (MMW).


## 2. Design of Antenna Element

The geometry of the single antenna element is shown in Figure1. The design is a combination of aperture coupled microstrip antenna (ACMPA) and a Horn antenna mounted on FR4 substrate, where the waveguide part of the horn is integrated into FR4 substrate. The model was designed and optimized using RF simulation software CST Microwave Studio and the results were reconfirmed via HFSS. The antenna is tuned to operate in a wide band of frequencies at 60 GHz. The multilayer antenna has three substrates with layers I and II having Rogers Duroid RT-5880 with ϵ
r
=
2.2 and tan
δ
=
0.003 and thickness t
1
=
0.127 mm and t
2
=
0.381 mm while the third layer has FR-4 as a substrate with ϵ
r
=
4.3 and thickness t
3
=
1.6 mm and a mounted Horn. The addition of FR4 has no other effect, except to provide support to the mounted Horn on the antenna performance. The ground with thickness (t
=
2
×
0.0175 mm) is made of conducting metal with a rectangular slot perpendicular to the microstrip feed having dimensions of L
s and W
s as given in Table 1. Coupling efficiencies between the aperture in the ground and the patch can be improved as investigated in [22]. The patch is located on the top of the substrate, at layer II, and has dimensions of L
p and W
p as given in Table 1. The dimensions of substrates and ground are taken as 30 × 30 mm2. The 50 Ω microstrip feed line at the bottom of lower substrate has a feed width of W
f
=
0.386 mm as calculated from Ansoft designer [23]. Table 1 shows the optimized values for the proposed antenna.Table 1
Parameters of proposed antenna in mm.
Design
Antenna element
Dimensions/parameters
Layer I
Microstrip feed
Feed width,W
f
=
0.386
Thickness,t
=
0.0175
Stub length,L
f
s
=
0.45
Substrate
RT Duroid 5880
Length,
L
=
30
Width,W
=
30
ϵ
r
=
2.2
tan
⁡
δ
=
0.003
Thickness,t
1
=
0.127
Ground
Thickness,t
=
0.0175
LengthL
=
30
WidthW
=
30
Thickness,t
=
0.0175
Rectangular slot
Slot length,L
s
=
1
Slot width,W
s
=
0.2
Layer II
Substrate
RT Duroid 5880
Thickness,t
2
=
0.381
ϵ
r
=
2.2
tan
⁡
δ
=
0.003
Length,L
=
30
Width,W
=
30
Patch
Length,L
p
=
1.2
Width,W
p
=
1.2
Layer III
Substrate
FR 4
Thickness,t
3
=
1.6
ϵ
r
=
4.3
tan
⁡
δ
=
0.025
Cut in FR-4
Length,L
f
r
=
3
Width,W
f
r
=
4.25
Horn
Horn dimensions
Horn length,
L
h
=
7.14
Horn width,W
h
=
7.14
Waveguide length,L
g
=
3
Waveguide width,W
g
=
4.25
Thickness of metal horn,t
=
2
Full structure
Total height
4Figure 1
Exploded view of proposed multilayer ACMPA with mounted Horn.With the aid of simulation tools, the proposed multilayer antenna was numerically optimized and the results were obtained. The objective was to achieve a wide bandwidth, high gain, and efficiency. Compared to [21], the impedance bandwidth improved significantly with almost the same gain. Due to the addition of 0.381 mm thickness substrate, the impedance bandwidth achieved was about 10.58% (58.9–65.25 GHz) with gain and efficiency of 11.78 dB and 88%, respectively. The simulation has taken into account the substrate and metallic losses. Figure 2 shows the bandwidth and gain comparison between two simulators for the single element antenna design. The two resonances seen in Figure 2 at 59.7 GHz and 63.5 GHz are due to the patch on layer II and the aperture of the Horn antenna integrated on it. Since this design is an extension of [21], the dimensions of the rectangular waveguide were optimized as given in Table 1. The initial length of the rectangular waveguide was chosen to be L
g
=
λ
0
/
2, which is a half wavelength at 60 GHz. The rectangular waveguide length has an effect on the reflection coefficient, which is minimum when L
g is around λ
0
/
2.Figure 2
Comparison of return loss and gain.Figures3(a) and 3(b) show the E-plane and H-plane radiation patterns, simulated in CST and HFSS, of the proposed antenna, for the frequencies at 59, 62, and 65 GHz, respectively. Thus for the multilayer structure at 62 GHz, the E-plane has side lobe of level −5 dB, half-power beamwidth of 31°, and a back radiation of −18.3 dB. The H-plane radiation pattern at 62 GHz has a side lobe of −13.2, half-power beamwidth of 69.8°, back radiation of −17 dB, and cross polarization level of >−30 dB.(a) Simulated E-plane radiation pattern at 59, 62, and 65 GHz and (b) simulated H-plane radiation pattern at 59, 62, and 65 GHz.
(a)
(b)


## 3. Design of Antenna Array

Limited methods exist in analyzing the antenna arrays. In the existing methods, arrays factor is the easiest one among others [6]. In simplest terms, array theory works on the principle that each antenna element is treated as an individual isotropic point source. Energy contributions from each point source are derived in the far field expressed as array factor (AF). The method of array factor is based on the theorem of orientation multiplying [6]:
(1)
AF
(
f
,
θ
)
=
∑
n
=
1
4
e
j
n
k
d
sin
θ
.The array factor depends only on the geometry of the array and the phase between each element. The actual radiator then replaces each point and the far field radiation pattern is determined by pattern multiplying the array factor with the pattern of the radiator. Mutual coupling is ignored in the process since the radiators are treated separately; also their influences on each other are not considered. Since we are working on improving the gain of the antenna, therefore, the mutual coupling cannot be ignored and the results deduced by array factor must be modified.


### 3.1. 2 × 2 Array

The next step is to improve the gain by making use of 2 × 2 and 4 × 4 arrays. The 3D exploded view of the 2 × 2 arrays structure is shown in Figure4, where a copper reflector element of distance λ/4 has been introduced below layer I to suppress the back radiations of the array. An important aspect in designing an array is the optimal distance between the patches or antenna elements to reduce mutual coupling among them. Mutual coupling has a noteworthy influence on the performance of antenna array. Mutual coupling affects several factors such as inputting resistance, orientation pattern of array, gain of the array, and its polarization [24–27]. In our proposed array design, center-to-center distances between patches were optimized from 0.5λ to 1λ that gave minimum coupling and maximum gain. The element spacing was selected to be 0.82λ
o in the x
-
y direction for both 2 × 2 and 4 × 4 arrays.Figure 4
Exploded view of 2 × 2 multilayer array withλ
/
4 reflector.A corporate feed network connected to a 50 Ω line was used as power division between antenna elements. Corporate feed networks are in general very versatile as they offer power splits of2
n (i.e., n
=
2,4
,
8,16,32, etc.) and control to the designer in terms of amplitude and phase selection of individual feed element and its power division among the transmission lines. It is ideal for scanning phased arrays, shaped-beam arrays, and multibeam arrays [6]. The length and width of the transmission lines can be varied as per requirement of power division. The feed network consists of 50 Ω transmission line and 70.7 Ω quarter-wavelength transformers matched to primary 50 Ω feeding line. The corporate feed network for 2 × 2 arrays is shown in Figure 5.Figure 5
Corporate-feed network for 2 × 2 array.Analyzing the top half of feed network shown in Figure5 and because of symmetry, two 50 Ω lines coming from each antenna are connected to two 70.7 Ω lines where each of them is a quarter wave transformer. This transforms each line into a 100 Ω line. Now we have two 100 Ω lines in parallel resulting in 50 Ω line. This 50 Ω is again connected to quarter wave transformer resulting in 100 Ω line. Similarly, another 100 Ω is available from the bottom half of the circuit resulting in a final 50 Ω line connected and matched to the main 50 Ω feed. The lengths and widths of 50 Ω and 70.7 Ω used in this feed network are shown in Table 2.Table 2
Lengths and widths of 50 Ω and 70.7 Ω feeds.
Transmission line
Width (mm)
Length (mm)
50 Ω
0.386
1.07
70.7 Ω
0.2262
0.93The proposed antenna of 2 × 2 array was simulated via simulation tools. Figure6 shows the comparison between simulators on the simulated return loss and gain for 2 × 2 arrays. Impedance bandwidth remains the same as 10.58% (58.9–65.25 GHz). The gain and efficiency are 15.3 dB and 88%, respectively. Due to the introduction of 0.381 mm substrate as compared to previous work [21], some parameters of the multilayer antenna design were optimized for the array structures to achieve wide bandwidth and impedance matching. The rest of the parameters were kept the same as presented in Table 1. The modified parameters are shown in Table 3.Table 3
Modified antenna parameters.
Parameters
2 × 2 array
4 × 4 array
Patch length,L
p
1.25
1.25
Patch width,W
p
1.25
1.25
Stub length,L
f
s
0.45
0.45
Horn length,L
h
r
12
12
Horn width,W
h
r
18
20Figure 6
Return loss and gain of 2 × 2 array.The E-plane and H-plane radiation patterns, simulated in CST and HFSS, for 2 × 2 array structure at frequencies 59, 62, and 65 GHz are shown in Figures7(a) and 7(b), respectively. It is observed that the E-plane at 62 GHz has a side lobe of level −13.7 dB, half-power beamwidth of 22.1°, and a back radiation of −25.3 dB. The H-plane radiation pattern at 62 GHz has a side lobe of −9.1 dB, half-power beamwidth of 22.2°, back radiation of −21.8 dB, and cross polarization level of >−30 dB.(a) E-plane radiation pattern at 59, 62, and 65 GHz for 2 × 2 array and (b) H-plane radiation pattern at 59, 62, and 65 GHz for 2 × 2 array.
(a)
(b)


### 3.2. 4 × 4 Array

Similarly, the 4 × 4 array was simulated and the comparison of results in terms of return loss and gain is shown in Figure8. Impedance bandwidth achieved is 10.58% (58.9–65.25 GHz) at 60 GHz. The gain and efficiency are 18.07 dB and 68.3%, respectively. Figures 9(a) and 9(b) show radiation patterns at 59, 62, and 65 GHz for 4 × 4 array. The E-plane at 62 GHz has a side lobe of level −11.8 dB, half-power beamwidth of 13.6°, and a back radiation of −23.07 dB. The H-plane radiation pattern at 62 GHz has a side lobe of −12.4, half-power beamwidth of 16.1°, and a back radiation of −23.07 dB. Table 4 shows the comparison of improved gain from single element to 2 × 2 and 4 × 4 arrays.Table 4
Simulated results of single element and 2 × 2 and 4 × 4 arrays.
Array/parameters
Single element
2 × 2 array
4 × 4 array
Bandwidth
10.58%
10.55%
10.51%
Gain
11.78 dB
15.3 dB
18.07 dB
Efficiency
88%
83%
68.3%Figure 8
Return loss and gain of 4 × 4 array.(a) E-plane radiation pattern at 59, 62, and 65 GHz for 4 × 4 array and (b) H-plane radiation pattern at 59, 62, and 65 GHz for 4 × 4 array.
(a)
(b)


## 3.1. 2 × 2 Array

The next step is to improve the gain by making use of 2 × 2 and 4 × 4 arrays. The 3D exploded view of the 2 × 2 arrays structure is shown in Figure4, where a copper reflector element of distance λ/4 has been introduced below layer I to suppress the back radiations of the array. An important aspect in designing an array is the optimal distance between the patches or antenna elements to reduce mutual coupling among them. Mutual coupling has a noteworthy influence on the performance of antenna array. Mutual coupling affects several factors such as inputting resistance, orientation pattern of array, gain of the array, and its polarization [24–27]. In our proposed array design, center-to-center distances between patches were optimized from 0.5λ to 1λ that gave minimum coupling and maximum gain. The element spacing was selected to be 0.82λ
o in the x
-
y direction for both 2 × 2 and 4 × 4 arrays.Figure 4
Exploded view of 2 × 2 multilayer array withλ
/
4 reflector.A corporate feed network connected to a 50 Ω line was used as power division between antenna elements. Corporate feed networks are in general very versatile as they offer power splits of2
n (i.e., n
=
2,4
,
8,16,32, etc.) and control to the designer in terms of amplitude and phase selection of individual feed element and its power division among the transmission lines. It is ideal for scanning phased arrays, shaped-beam arrays, and multibeam arrays [6]. The length and width of the transmission lines can be varied as per requirement of power division. The feed network consists of 50 Ω transmission line and 70.7 Ω quarter-wavelength transformers matched to primary 50 Ω feeding line. The corporate feed network for 2 × 2 arrays is shown in Figure 5.Figure 5
Corporate-feed network for 2 × 2 array.Analyzing the top half of feed network shown in Figure5 and because of symmetry, two 50 Ω lines coming from each antenna are connected to two 70.7 Ω lines where each of them is a quarter wave transformer. This transforms each line into a 100 Ω line. Now we have two 100 Ω lines in parallel resulting in 50 Ω line. This 50 Ω is again connected to quarter wave transformer resulting in 100 Ω line. Similarly, another 100 Ω is available from the bottom half of the circuit resulting in a final 50 Ω line connected and matched to the main 50 Ω feed. The lengths and widths of 50 Ω and 70.7 Ω used in this feed network are shown in Table 2.Table 2
Lengths and widths of 50 Ω and 70.7 Ω feeds.
Transmission line
Width (mm)
Length (mm)
50 Ω
0.386
1.07
70.7 Ω
0.2262
0.93The proposed antenna of 2 × 2 array was simulated via simulation tools. Figure6 shows the comparison between simulators on the simulated return loss and gain for 2 × 2 arrays. Impedance bandwidth remains the same as 10.58% (58.9–65.25 GHz). The gain and efficiency are 15.3 dB and 88%, respectively. Due to the introduction of 0.381 mm substrate as compared to previous work [21], some parameters of the multilayer antenna design were optimized for the array structures to achieve wide bandwidth and impedance matching. The rest of the parameters were kept the same as presented in Table 1. The modified parameters are shown in Table 3.Table 3
Modified antenna parameters.
Parameters
2 × 2 array
4 × 4 array
Patch length,L
p
1.25
1.25
Patch width,W
p
1.25
1.25
Stub length,L
f
s
0.45
0.45
Horn length,L
h
r
12
12
Horn width,W
h
r
18
20Figure 6
Return loss and gain of 2 × 2 array.The E-plane and H-plane radiation patterns, simulated in CST and HFSS, for 2 × 2 array structure at frequencies 59, 62, and 65 GHz are shown in Figures7(a) and 7(b), respectively. It is observed that the E-plane at 62 GHz has a side lobe of level −13.7 dB, half-power beamwidth of 22.1°, and a back radiation of −25.3 dB. The H-plane radiation pattern at 62 GHz has a side lobe of −9.1 dB, half-power beamwidth of 22.2°, back radiation of −21.8 dB, and cross polarization level of >−30 dB.(a) E-plane radiation pattern at 59, 62, and 65 GHz for 2 × 2 array and (b) H-plane radiation pattern at 59, 62, and 65 GHz for 2 × 2 array.
(a)
(b)


## 3.2. 4 × 4 Array

Similarly, the 4 × 4 array was simulated and the comparison of results in terms of return loss and gain is shown in Figure8. Impedance bandwidth achieved is 10.58% (58.9–65.25 GHz) at 60 GHz. The gain and efficiency are 18.07 dB and 68.3%, respectively. Figures 9(a) and 9(b) show radiation patterns at 59, 62, and 65 GHz for 4 × 4 array. The E-plane at 62 GHz has a side lobe of level −11.8 dB, half-power beamwidth of 13.6°, and a back radiation of −23.07 dB. The H-plane radiation pattern at 62 GHz has a side lobe of −12.4, half-power beamwidth of 16.1°, and a back radiation of −23.07 dB. Table 4 shows the comparison of improved gain from single element to 2 × 2 and 4 × 4 arrays.Table 4
Simulated results of single element and 2 × 2 and 4 × 4 arrays.
Array/parameters
Single element
2 × 2 array
4 × 4 array
Bandwidth
10.58%
10.55%
10.51%
Gain
11.78 dB
15.3 dB
18.07 dB
Efficiency
88%
83%
68.3%Figure 8
Return loss and gain of 4 × 4 array.(a) E-plane radiation pattern at 59, 62, and 65 GHz for 4 × 4 array and (b) H-plane radiation pattern at 59, 62, and 65 GHz for 4 × 4 array.
(a)
(b)


## 4. Conclusion

A high gain and wide band multilayer antenna for 60 GHz are proposed in this paper. Stacked structure technique employing aperture coupled feeding with mounted Horn antenna is employed as the radiator for the single element, 2 × 2 and 4 × 4 arrays. The proposed antenna exhibits a broad impedance bandwidth of about 10.5% (58.9–65.25 GHz). Comprised by the proposed antenna element, an antenna array is investigated. Simulated results in CST and HFSS show that the antenna array realized provides a maximum gain and efficiency of 18.07 dB and 68.3%, respectively. The proposed antenna finds application in V-band communication systems.



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*Source: 418056-2014-04-22.xml*