# Unknown Disturbance Estimation for a PMSM with a Hybrid Sliding Mode Observer

Authors: Gang Chen; Yong Zhou; TingTing Gao; Qicai Zhou
Journal: Mathematical Problems in Engineering
 (2015)

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## Abstract

A hybrid sliding mode observer that
combines high gain feedback and a high-order sliding mode
term is developed to identify the time-varying disturbance for
a permanent-magnet synchronous motor (PMSM). Based on the
measurable current and the position, the unknown disturbance
can be identified from the sliding mode term without digital
filter effect. It is then used to enhance the robustness of the
speed control dynamics. For ease of implementation in real
applications, such as DSP and FPGA, the proposed observer
is properly designed to avoid complex mathematical operators.
Simulation results are given to illustrate the performance of the proposed observer.


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## Body

## 1. Introduction

In real industrial application, the unknown disturbance on a permanent-magnet synchronous motor (PMSM) is inevitable and it limits the performance of the controlled processes. For such a situation, a robust observer with high estimation accuracy is required to recover the uncertainty in real time.The sliding-mode-based observer has been proven to be an effective approach for handling uncertain systems, due to its capability of reconstructing the uncertainties based on the equivalent injection input concept [1–3], and there are many effective results presented during past years [4–13]. In [14], a sliding mode flux observer is developed for an induction motor, and the unknown rotor resistance can be reconstructed from a switching function after the sliding surface driven to zero. In [15, 16], the sliding mode observer is used to identify the back-EMFs for a PMSM. However, such results require a low-pass filter for the uncertainties reconstruction because of the discontinuous switching feedback, and the uncertainty estimation accuracy is greatly dependent on the low-pass filter parameters.To improve the estimation accuracy by removing the filtering effect, some existing works have suggested the usage of a saturation function to replace the switching term [17–19]. However, this results in a trade-off between the robustness of observer and the estimation accuracy of uncertainty. Another existing method is based on the higher-order sliding mode techniques, by treating the derivatives of the system input as a new control signal, which results in a continuous integral function of the switching term; then the chattering/filtering effect can be avoided [20, 21].Another problem is that the sliding mode gains have to be chosen large enough to ensure the stability of the observer, which is usually related to the system initial values. To solve this problem, a hybrid observer that combines high gain feedback and higher-order sliding mode observer has been proposed in [22], in which the high gain feedback works to constrain the estimation error within an invariant set regardless of initial values; then the sliding mode gains can be designed to ensure the global stability of the observer. Such hybrid observers have been applied into a series DC motor for the speed estimation and unknown time-varying parameter identification for a DC motor [23].In this paper, we will consider the unknown disturbance estimation for a permanent-magnet synchronous motor. A hybrid sliding mode observer is developed for the disturbance identification. The most challenging problem is how to properly design the observer algorithm to simplify the observer implementation in real applications, such as in a digital signal processor (DSP) and FPGA. The contribution of this work can be summarized as follows.(1)
With the proposed observer, the disturbanceTL can be asymptotically estimated and then used to enhance the robustness of the speed control dynamics. The theoretical analysis and simulation results are given to demonstrate the effectiveness of the proposed observer.(2)
A hybrid observer structure is adopted, in which the high gain feedback term works to speed up the convergence time and guarantees the sliding mode gain design is independent of the system initial values.(3)
For disturbance identification, the digital filtering effect is successfully avoided without sacrificing robustness of the observer.(4)
The twisting sliding mode algorithm is properly integrated in the proposed observer, to make the observer ease for implementation in real application.The remainder of this paper is organized as follows. Section2 introduces the mathematical mode of the PMSM and some background results are presented. In Section 3, a speed observer and a disturbance are developed to identify the unknown external load disturbance. In Section 4, some simulations are provided to illuminate the effectiveness of the two proposed observers. Section 5 concludes this paper.


## 2. Preliminary

### 2.1. Mathematical Model

The state equation of a surface-mounted magnet brushless AC motor in stationaryα-β reference frame is given by [24]:(1)i˙α=-RLiα+λmLωsinθ+uαL,i˙β=-RLiβ-λmLωcosθ+uβL,θ˙=ω,(2)ω˙=32p2Jλm-iαsinθ+iβcosθ-BJω-pTLJ,where iα,β is the state current in α-β reference frame, uα,β is the state voltage in α-β reference frame, R is the resistance, L is the inductance, λm is the flux-linkage due to permanent magnet, θ is the rotor position, ω is the electrical angular speed, J is the rotor moment of inertia, B is the viscous-friction coefficient, and TL is the load torque.Here, the load torqueTL is assumed to be the system uncertainty that includes the unknown external disturbance, the parameter variations of rotor inertia, and the viscous-friction coefficient.The target of this paper is to develop a robust and high accuracy observer that can identify the unknown disturbanceTL, based on the measurable current, voltage, and rotor position.


### 2.2. Background Results

Consider an uncertain nonlinear system in the form of(3)x˙=Ax+αx,u+Pxdt,y=Cx,where x=[x1,x2,…,xn]T∈Rn and(4)A=0n-1×1In-1×n-101×101×n-1,C=10⋯0∈Rnare constant matrices; d(t)∈R denotes the lumped system uncertainty; u is the system input; the nonlinear functions α(x,u) and P(x) are smooth Lipschitz vectors with triangular structures, it has(5)αx=0,…,0,αrx1,…,xr,…,αnx1,…,xnT,Px=0,…,0,1,pr+1x1,…,xr,…,pnx1,…,xnTwith r being the relative degree order between the disturbance d(t) and the measurable output y.Then, a hybrid observer that combines high gain feedback with higher-order sliding mode can be designed as [22](6)x^˙=Ax^+αx^,u+Ly-Cx^+Px^krur,u˙r=0,ifur≥u¯r,v,ifur<u¯r,where L is the high gain linear feedback parameter, given by(7)L=l1l2⋯lnT∈Rn,and kr is a positive tuning parameter of nonlinear feedback ur, which is designed as an integral function of a (r+1)th-order sliding mode term v; u¯r denotes the upper bound of ur.It has been proven in [22] that the high gain feedback term works to constrain the estimation error to within an invariant set and the nonlinear term krur will asymptotically track the unknown disturbance d(t) without digital filtering effect if we properly design the sliding mode feedback term.The mechanical dynamics given in (2) can be considered as a second-order nonlinear system in (3), with the relative degree order between the disturbance and the measurable output being two; that is, r=n=2, d(t)=-pTL/J. Then, one can design a hybrid observer in the form of (6), with v being third-order sliding mode feedback. However, to the best of our understanding, the existing third-order or higher-order sliding mode algorithms involve complex math operations that require more computation resources in real implementation, such as in digital signal processor and FPGA.In next section, we will design a hybrid observer that is based on the second-order twisting sliding mode algorithm [1]; the most advantage of such sliding algorithm is that it only requires the sign of the first derivative operator, but not its real value. Thus, the proposed observer takes less computation resources and is easy for implementation in digital signal processor.


## 2.1. Mathematical Model

The state equation of a surface-mounted magnet brushless AC motor in stationaryα-β reference frame is given by [24]:(1)i˙α=-RLiα+λmLωsinθ+uαL,i˙β=-RLiβ-λmLωcosθ+uβL,θ˙=ω,(2)ω˙=32p2Jλm-iαsinθ+iβcosθ-BJω-pTLJ,where iα,β is the state current in α-β reference frame, uα,β is the state voltage in α-β reference frame, R is the resistance, L is the inductance, λm is the flux-linkage due to permanent magnet, θ is the rotor position, ω is the electrical angular speed, J is the rotor moment of inertia, B is the viscous-friction coefficient, and TL is the load torque.Here, the load torqueTL is assumed to be the system uncertainty that includes the unknown external disturbance, the parameter variations of rotor inertia, and the viscous-friction coefficient.The target of this paper is to develop a robust and high accuracy observer that can identify the unknown disturbanceTL, based on the measurable current, voltage, and rotor position.


## 2.2. Background Results

Consider an uncertain nonlinear system in the form of(3)x˙=Ax+αx,u+Pxdt,y=Cx,where x=[x1,x2,…,xn]T∈Rn and(4)A=0n-1×1In-1×n-101×101×n-1,C=10⋯0∈Rnare constant matrices; d(t)∈R denotes the lumped system uncertainty; u is the system input; the nonlinear functions α(x,u) and P(x) are smooth Lipschitz vectors with triangular structures, it has(5)αx=0,…,0,αrx1,…,xr,…,αnx1,…,xnT,Px=0,…,0,1,pr+1x1,…,xr,…,pnx1,…,xnTwith r being the relative degree order between the disturbance d(t) and the measurable output y.Then, a hybrid observer that combines high gain feedback with higher-order sliding mode can be designed as [22](6)x^˙=Ax^+αx^,u+Ly-Cx^+Px^krur,u˙r=0,ifur≥u¯r,v,ifur<u¯r,where L is the high gain linear feedback parameter, given by(7)L=l1l2⋯lnT∈Rn,and kr is a positive tuning parameter of nonlinear feedback ur, which is designed as an integral function of a (r+1)th-order sliding mode term v; u¯r denotes the upper bound of ur.It has been proven in [22] that the high gain feedback term works to constrain the estimation error to within an invariant set and the nonlinear term krur will asymptotically track the unknown disturbance d(t) without digital filtering effect if we properly design the sliding mode feedback term.The mechanical dynamics given in (2) can be considered as a second-order nonlinear system in (3), with the relative degree order between the disturbance and the measurable output being two; that is, r=n=2, d(t)=-pTL/J. Then, one can design a hybrid observer in the form of (6), with v being third-order sliding mode feedback. However, to the best of our understanding, the existing third-order or higher-order sliding mode algorithms involve complex math operations that require more computation resources in real implementation, such as in digital signal processor and FPGA.In next section, we will design a hybrid observer that is based on the second-order twisting sliding mode algorithm [1]; the most advantage of such sliding algorithm is that it only requires the sign of the first derivative operator, but not its real value. Thus, the proposed observer takes less computation resources and is easy for implementation in digital signal processor.


## 3. Observer Design

Consider the mechanical dynamic system described in (2); the rotor position θ is measurable, and the target is to estimate the unknown disturbance TL, as well as the angular speed ω.It is well-known that there are many methodologies to estimate the angular speedω based on the measurable position θ. One common method is based on the back-forward differentiator; that is, ω^k=[θk-θ(k-1)]/Ts, where Ts is the sampling time and subscript k denotes the variable value at time t=kTs. For such method, the estimation error is proportional to sampling time. On the other hand, small sampling time may enlarge the numerical error of (θk-θk-1), especially at low rotor speed and low position sensor resolution situation.As mentioned in the previous section, in order to simplify the hybrid observer structure and remove the digital filtering effect, we will consider using the second-order twisting algorithm for the unknown disturbance estimation.The system diagram is shown in Figure1. The first observer (speed observer) will be performed to identify the rotor speed without involving the operation of inverse of sampling time, that is, 1/Ts. Then the second observer (disturbance observer) ensures the unknown disturbance TL can be identified online without digital filtering effect. Finally, one can use the identified disturbance to compensate the control loop to improve the robustness of the control system.Figure 1
System diagram.


### 3.1. Speed Observer

By considering the rotor speedω as the system uncertainty, a hybrid sliding mode observer is designed in the form of(8)θ^˙=-l1e1+u1,where e1≜θ^-θ, l1 is a positive high gain parameter, and u1 is the nonlinear feedback which is given by(9)u˙1=0,ifu1≥u¯1,v1,ifu1<u¯1,v1=-ρ11signθ^-θ-ρ12signθ^˙-θ˙.Here, u¯1 is the upper bound of the nonlinear feedback term, and it is chosen large enough, as u¯1≥|ω|. Then, ρ11 and ρ12 are the properly chosen positive sliding gains.Theorem 1.
With the proposed hybrid observer given in (8) and (9), the rotor speed can be asymptotically identified by properly choosing the observer parameters; that is, it will have ω=u1.Proof.
Compare the equations in (2) and (8); the estimation error dynamic of e1 can be written as(10)e˙1=-l1e1-ω+u1.By defining a Lyapunov function V1=|e1|2/2, it has(11)V˙1=-l1e12-ωe1+u1e1≤e1-l1e1+ω+u¯1≤e1-l1e1+2u¯1choosingu¯1≥ωwhich implies that, after some time, the estimation error e1 will converge into an invariant set regardless of initial value of θ; that is, |e1|≤2u¯1/l1.
Now, assumingu1<u¯1, we consider the new dynamic by taking the derivative on both sides of (10); it has(12)e¨1=-l1e˙1-ω˙+v1=l12e1+l1ω-l1u1-ω˙+v1≜d1t+v1with d1(t) denoting dynamic terms (l12e1+l1ω-l1u1-ω˙), which is assumed to be bounded with d¯1. Then, by defining the second Lyapunov function V2=|e˙1|2/2+ρ11|e1|, which is continuously differentiable except on e1=0, it can be verified that(13)V˙2=e˙1e¨1+ρ11e˙1signe1=e˙1d1t-ρ11signe1-ρ12signe˙1+ρ11e˙1signe1=e˙1d1t-ρ12signe˙1≤e˙1d¯1-ρ12which implies that it has V˙2<0 if the sliding gains are chosen large enough; that is, ρ11>ρ12>d¯1. In other words, the second-order sliding surface e˙1=e1=0 will be reached in a finite time and remained thereafter. Then, the rotor speed can be directly obtained from (9), as ω=u1.Remark 2.
In real implementation, the derivatives in (9) can be replaced with their backward differentiators, respectively; that is, v1k=-ρ11sign(e1k)-ρ12sign(e1k-e1(k-1)). The subscript k denotes the variables obtained at sampling time t=kTs. Note that the operation of 1/Ts is completely avoided; then one can increase the sampling and control frequency without sacrificing its related numerical accuracy.


### 3.2. Disturbance Observer

With the identified rotor speed, a hybrid disturbance observer is designed in the form of(14)ω^˙=32p2Jλm-iαsinθ+iβcosθ-BJω^-l2e2-pu2J,u˙2=0,ifu2≥u¯2,v2,ifu2<u¯2,v2=-ρ21signω^-u1-ρ22signω^˙-u˙1,where e2≜ω^-u1; l2 is a positive high gain parameter; ρ21 and ρ22 are two properly chosen positive sliding gains; u¯2 is the upper bound of the nonlinear feedback u2, which is designed as an integral function of a sliding mode term v2.Theorem 3.
With the proposed speed observer in (8) and the disturbance observer in (14), the system unknown disturbance TL can be identified in finite time if properly choosing the observer parameters; that is, it will have TL=u2.Proof.
According to the result in Theorem1, the rotor speed ω can be identified from u1 after some time; therefore, the dynamics of the estimation error e2=ω^-u1=ω^-ω can be deduced from (2) and (14) as(15)e˙2=-BJe2-l2e2+pTLJ-pu2J.
Noting that the dynamic form in (15) is similar to the one in (10), then it can be proven that the second-order sliding surface e˙2=e2=0 will be reached and remained thereafter in finite time, if properly choosing the observer parameters; that is, u¯2>|TL|; ρ21 and ρ22 are chosen large enough.
By substituting the sliding surfacee˙2=e2=0 into the estimation error dynamics in (15), it has(16)TL=u2which means the unknown disturbance can be directly obtained from u2 without digital filtering effect.Remark 4.
In real implementation, the derivatives in (14) can be replaced with their backward differentiators, respectively; that is, v2k=-ρ21sign(e2k)-ρ22sign(e2k-e2(k-1)). Then, the operation of 1/Ts is completely avoided.


## 3.1. Speed Observer

By considering the rotor speedω as the system uncertainty, a hybrid sliding mode observer is designed in the form of(8)θ^˙=-l1e1+u1,where e1≜θ^-θ, l1 is a positive high gain parameter, and u1 is the nonlinear feedback which is given by(9)u˙1=0,ifu1≥u¯1,v1,ifu1<u¯1,v1=-ρ11signθ^-θ-ρ12signθ^˙-θ˙.Here, u¯1 is the upper bound of the nonlinear feedback term, and it is chosen large enough, as u¯1≥|ω|. Then, ρ11 and ρ12 are the properly chosen positive sliding gains.Theorem 1.
With the proposed hybrid observer given in (8) and (9), the rotor speed can be asymptotically identified by properly choosing the observer parameters; that is, it will have ω=u1.Proof.
Compare the equations in (2) and (8); the estimation error dynamic of e1 can be written as(10)e˙1=-l1e1-ω+u1.By defining a Lyapunov function V1=|e1|2/2, it has(11)V˙1=-l1e12-ωe1+u1e1≤e1-l1e1+ω+u¯1≤e1-l1e1+2u¯1choosingu¯1≥ωwhich implies that, after some time, the estimation error e1 will converge into an invariant set regardless of initial value of θ; that is, |e1|≤2u¯1/l1.
Now, assumingu1<u¯1, we consider the new dynamic by taking the derivative on both sides of (10); it has(12)e¨1=-l1e˙1-ω˙+v1=l12e1+l1ω-l1u1-ω˙+v1≜d1t+v1with d1(t) denoting dynamic terms (l12e1+l1ω-l1u1-ω˙), which is assumed to be bounded with d¯1. Then, by defining the second Lyapunov function V2=|e˙1|2/2+ρ11|e1|, which is continuously differentiable except on e1=0, it can be verified that(13)V˙2=e˙1e¨1+ρ11e˙1signe1=e˙1d1t-ρ11signe1-ρ12signe˙1+ρ11e˙1signe1=e˙1d1t-ρ12signe˙1≤e˙1d¯1-ρ12which implies that it has V˙2<0 if the sliding gains are chosen large enough; that is, ρ11>ρ12>d¯1. In other words, the second-order sliding surface e˙1=e1=0 will be reached in a finite time and remained thereafter. Then, the rotor speed can be directly obtained from (9), as ω=u1.Remark 2.
In real implementation, the derivatives in (9) can be replaced with their backward differentiators, respectively; that is, v1k=-ρ11sign(e1k)-ρ12sign(e1k-e1(k-1)). The subscript k denotes the variables obtained at sampling time t=kTs. Note that the operation of 1/Ts is completely avoided; then one can increase the sampling and control frequency without sacrificing its related numerical accuracy.


## 3.2. Disturbance Observer

With the identified rotor speed, a hybrid disturbance observer is designed in the form of(14)ω^˙=32p2Jλm-iαsinθ+iβcosθ-BJω^-l2e2-pu2J,u˙2=0,ifu2≥u¯2,v2,ifu2<u¯2,v2=-ρ21signω^-u1-ρ22signω^˙-u˙1,where e2≜ω^-u1; l2 is a positive high gain parameter; ρ21 and ρ22 are two properly chosen positive sliding gains; u¯2 is the upper bound of the nonlinear feedback u2, which is designed as an integral function of a sliding mode term v2.Theorem 3.
With the proposed speed observer in (8) and the disturbance observer in (14), the system unknown disturbance TL can be identified in finite time if properly choosing the observer parameters; that is, it will have TL=u2.Proof.
According to the result in Theorem1, the rotor speed ω can be identified from u1 after some time; therefore, the dynamics of the estimation error e2=ω^-u1=ω^-ω can be deduced from (2) and (14) as(15)e˙2=-BJe2-l2e2+pTLJ-pu2J.
Noting that the dynamic form in (15) is similar to the one in (10), then it can be proven that the second-order sliding surface e˙2=e2=0 will be reached and remained thereafter in finite time, if properly choosing the observer parameters; that is, u¯2>|TL|; ρ21 and ρ22 are chosen large enough.
By substituting the sliding surfacee˙2=e2=0 into the estimation error dynamics in (15), it has(16)TL=u2which means the unknown disturbance can be directly obtained from u2 without digital filtering effect.Remark 4.
In real implementation, the derivatives in (14) can be replaced with their backward differentiators, respectively; that is, v2k=-ρ21sign(e2k)-ρ22sign(e2k-e2(k-1)). Then, the operation of 1/Ts is completely avoided.


## 4. Simulation Result

In this section, we consider the simulation on a PMSM with its parameters being given in Table1.Table 1
Parameters of a PMSM.
Pole pairs
p
4
Rating speed
ω
600 rad/s
Resistance
R
2.5Ω
Inductance
L
8 mH
Inertia
J
0.00027 kg·m2
Viscous-friction coefficient
B
0.04 N·m/rad/s
Field flux-related coefficient
λ
m
0.041 N·m/Wb·ATo demonstrate the proposed observers performance, a speed open loop control platform is used, with the unknown torque disturbance given asTL=4sin(5t)+3cos(2t) N·m. Then, the estimation performance among a traditional high gain observer, a pure higher-order sliding mode observer, and the proposed hybrid observer is carefully compared.Furthermore, the speed closed loop control performance with and without the compensation from identified disturbance is also addressed.


### 4.1. Traditional High Gain Observer

First, a traditional high gain observer is applied by setting the sliding mode feedback terms in (9) and (14) to zeros; that is, u1=0, u2=0, and e2≜ω^-ω. And the high gain parameters are chosen as l1=20 and l2=20. The initial rotor position and speed are set to ω(0)=50 rad/s and θ(0)=200 rad. Then, the simulation result is shown in Figure 2.Figure 2
Traditional high gain observer.It can be seen that the high gain observer failed to estimate the unknown disturbance as it does not have any mechanism to identify it.


### 4.2. Pure Sliding Mode Observer

Then, a pure sliding mode observer is used to identify the unknown disturbance by setting the high gains in (8) and (14) to zeros; that is, l1=0 and l2=0. Then, the sliding mode parameters are chosen as k11=1700, k12=800, k21=51, and k22=20. The initial conditions are chosen the same as above.The simulation result is shown in Figure3. Here, we can see that the unknown disturbance can be successfully identified after around 2.4 seconds when the sliding mode surfaces are reached.Figure 3
Pure sliding mode observer.


### 4.3. Proposed Hybrid Sliding Mode Observer

Last, the proposed hybrid sliding mode observers in (8)–(14) are applied. The parameters and initial conditions are chosen the same as above, and the simulation result is shown in Figure 4.Figure 4
Proposed hybrid sliding mode observer.It is clear that, with the proposed hybrid sliding mode observer, the unknown disturbanceTL can be identified with high accuracy and much faster than the pure sliding mode observer because of the additional high gain feedback terms.


### 4.4. Closed Loop Control without Disturbance Compensation

Now, we consider the speed closed loop control system with unknown disturbance and the system diagram is given in Figure1.First, by removing the disturbance compensation from the speed feedback loop, that is, settingT^L=0, the simulation of speed closed loop control system under a periodic and trapezoidal unknown disturbance is given in Figures 5 and 6.Figure 5
Closed loop control without disturbance compensation 1.Figure 6
Closed loop control without disturbance compensation 2.It can be seen that 300 rad/sec maximin speed transient is observed when the disturbance changes from+4 N·m to -4 N·m at time of 2 seconds.


### 4.5. Closed Loop Control with Disturbance Compensation

Then, by setting the disturbance compensation in the speed feedback control loop, that is,T^L=u2, all the controller and observer parameters are chosen the same as previous.The simulation results are shown in Figures7 and 8 and around 100 rad/sec speed transient is observed when the disturbance changes from +4 N·m to -4 N·m, which means the robustness of the speed closed loop controller is improved with the disturbance compensation.Figure 7
Closed loop control with disturbance compensation 1.Figure 8
Closed loop control with disturbance compensation 2.


## 4.1. Traditional High Gain Observer

First, a traditional high gain observer is applied by setting the sliding mode feedback terms in (9) and (14) to zeros; that is, u1=0, u2=0, and e2≜ω^-ω. And the high gain parameters are chosen as l1=20 and l2=20. The initial rotor position and speed are set to ω(0)=50 rad/s and θ(0)=200 rad. Then, the simulation result is shown in Figure 2.Figure 2
Traditional high gain observer.It can be seen that the high gain observer failed to estimate the unknown disturbance as it does not have any mechanism to identify it.


## 4.2. Pure Sliding Mode Observer

Then, a pure sliding mode observer is used to identify the unknown disturbance by setting the high gains in (8) and (14) to zeros; that is, l1=0 and l2=0. Then, the sliding mode parameters are chosen as k11=1700, k12=800, k21=51, and k22=20. The initial conditions are chosen the same as above.The simulation result is shown in Figure3. Here, we can see that the unknown disturbance can be successfully identified after around 2.4 seconds when the sliding mode surfaces are reached.Figure 3
Pure sliding mode observer.


## 4.3. Proposed Hybrid Sliding Mode Observer

Last, the proposed hybrid sliding mode observers in (8)–(14) are applied. The parameters and initial conditions are chosen the same as above, and the simulation result is shown in Figure 4.Figure 4
Proposed hybrid sliding mode observer.It is clear that, with the proposed hybrid sliding mode observer, the unknown disturbanceTL can be identified with high accuracy and much faster than the pure sliding mode observer because of the additional high gain feedback terms.


## 4.4. Closed Loop Control without Disturbance Compensation

Now, we consider the speed closed loop control system with unknown disturbance and the system diagram is given in Figure1.First, by removing the disturbance compensation from the speed feedback loop, that is, settingT^L=0, the simulation of speed closed loop control system under a periodic and trapezoidal unknown disturbance is given in Figures 5 and 6.Figure 5
Closed loop control without disturbance compensation 1.Figure 6
Closed loop control without disturbance compensation 2.It can be seen that 300 rad/sec maximin speed transient is observed when the disturbance changes from+4 N·m to -4 N·m at time of 2 seconds.


## 4.5. Closed Loop Control with Disturbance Compensation

Then, by setting the disturbance compensation in the speed feedback control loop, that is,T^L=u2, all the controller and observer parameters are chosen the same as previous.The simulation results are shown in Figures7 and 8 and around 100 rad/sec speed transient is observed when the disturbance changes from +4 N·m to -4 N·m, which means the robustness of the speed closed loop controller is improved with the disturbance compensation.Figure 7
Closed loop control with disturbance compensation 1.Figure 8
Closed loop control with disturbance compensation 2.


## 5. Conclusion

Based on the measurable current and rotor position, a hybrid sliding mode observer is developed for the unknown disturbance estimation on a permanent-magnetic AC motor. The proposed observer has a simple structure and ease for real implementation in digital signal processor, and the unknown disturbance will be identified without digital filtering effect. Moreover, the identified disturbance can be used to compensate online the speed closed loop control system to improve the robustness.



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