# Dual-Band 2 × 2 MIMO Antenna with Compact Size and High Isolation Based on Half-Mode SIW

Authors: Abubaker Ahmed Elobied; Xue-Xia Yang; Ningjie Xie; Steven Gao
Journal: International Journal of Antennas and Propagation
 (2020)

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## Abstract

This paper presents a close-spaced dual-band 2 × 2 multiple-input multiple-output (MIMO) antenna with high isolation based on half-mode substrate integrated waveguide (HMSIW). The dual-band operation of the antenna element is achieved by loading a rectangular patch outside the radiating aperture of an HMSIW cavity. The HMSIW cavity is excited by a coaxial probe, whereas the rectangular patch is energized through proximity coupling by the radiating aperture of HMSIW. The antenna elements can be closely placed using the rotation and orthogonal arrangement for a 2 × 2 array. Small neutralization lines at the center of the MIMO antenna can increase the isolation among its elements by around 10 dB in the lower band and 5 dB in the higher band. A prototype of the MIMO antenna is fabricated and its performance is measured. The measured results show that the resonant frequencies are centered at 4.43 and 5.39 GHz with bandwidths of 110 and 80 MHz and peak gains of 6 and 6.4 dBi, respectively. The minimum isolation in both bands is greater than 35 dB. The envelope correlation coefficient is lower than 0.005 within two operating bands.


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## Body

## 1. Introduction

Antenna systems that support multiple wireless standards and have compact size are highly desirable for future portable devices. Multiple-input multiple-output (MIMO) antenna technology has become essential for future portable devices owing to its ability to increase data throughput without increasing the power and bandwidth [1]. Therefore, developing compact multiband antennas to support multifunctional MIMO systems is necessary. High isolation among the elements of a compact dual-band MIMO antenna is important for the performance of a communication system.Some dual-band MIMO antennas obtained using different decoupling techniques have been introduced in the literature; these are generally summarized into two types. The first type involves decoupling antenna elements without inserting any decoupling structures; here, the decoupling could be realized using spatial [2], pattern [3], and polarization diversities [4]. Spatial diversity can be achieved by arranging two or more antenna elements such that there is a wide space between them; therefore, such MIMO antennas have a large size. Pattern diversity can be realized by discriminating antenna elements over an angled space, whereas polarization diversity can be achieved by orthogonally arranging the antenna elements. Pattern and polarization diversities are preferred because the elements can be arranged close to each other. However, the coupling is difficult to control when more than two closely spaced antennas are employed.The second type of decoupling for MIMO antenna involves inserting a decoupling structure between the antenna elements to block or suppress the coupling, which includes defected ground structure [5], complementary split-ring resonator [6], electromagnetic bandgap [7], neutralization line [8], T-shaped stub [9], and ring strip [10]. However, these structures increase the space between antenna elements, which results in larger antenna sizes. High isolation can be achieved by combining the two methods above [11–15].In this paper, a dual-band antenna element is proposed by loading a rectangular patch outside the aperture of a half-mode substrate integrated waveguide (HMSIW) cavity. By combining the spatial and polarization diversities and using small neutralization lines (SNLs), a close-spaced 2 × 2 MIMO antenna with high isolation and dual-band operation is suggested. To validate the proposed antenna, a prototype is fabricated and its performance is measured. This paper is arranged as follows. In Section2, the design procedure of the proposed dual-band antenna element is discussed. In Section 3, four-element MIMO antennas are introduced and their corresponding decoupling mechanisms are explained. The fabrication and measurement results are presented in Section 4. The conclusion of the proposed work is presented in Section 5.


## 2. Dual-Band Antenna Element

A dual-band antenna element obtained by loading a rectangular patch outside an HMSIW cavity is proposed, as shown in Figure1. The antenna element has only one substrate layer, and the bottom side of the substrate is a metallic ground plane. The HMSIW antenna is fed by a coaxial probe, whereas the patch antenna is excited through proximity coupling by the radiating aperture of the HMSIW antenna. The HMSIW antenna generates the lower band, whereas the loading patch generates the upper band.Figure 1
Construction of the proposed antenna element.The geometrical size of the proposed dual-band antenna element is shown in Figure2. The size of the HMSIW cavity is W × W and the dimensions of the patch are Lp × Wp. The coupling gap is designated as G. To be equivalent to a conventional metallic cavity, the diameter d and pitch s of the HMSIW cavity via holes must meet the conditions of d/s ≥ 0.5 and d/λ0 ≤ 0.1 [16].Figure 2
Geometry of the proposed dual-band antenna element. (a) Top view and (b) bottom view.
(a)(b)The antenna element was designed on a single-layer substrate of Rogers Duroid 5880 with a relative dielectric constant of 2.2, tangent loss of 0.0009, and thickness of 1.57 mm. A high-frequency structure simulator was used to analyze and simulate the antenna. The optimum parameters of the proposed antenna element areW = 40 mm, Lp = 18 mm, Wp = 20 mm, and G = 0.4 mm. The simulated reflection coefficient of the proposed dual-band antenna is depicted in Figure 3. The two simulated resonances appear at 4.46 and 5.38 GHz.Figure 3
Simulated reflection coefficient of the proposed dual-band antenna.Figure4 depicts the simulated electric field distributions at fL = 4.46 GHz and fH = 5.38 GHz. Figure 4(a) illustrates that the power is concentrated along the edge of the aperture of the HMSIW cavity, which implies that the resonant mode at fL = 4.46 GHz is generated by the HMSIW cavity. In contrast, the electric field is mainly concentrated along the two edges of the patch at fH = 5.38 GHz, as observed in Figure 4(b).Figure 4
Simulated electric field distribution on the dual-band antenna at the two resonant frequencies: (a)fL = 4.46 GHz and (b) fH = 5.38 GHz.
(a)(b)


## 3. Dual-Band 2 × 2 MIMO Antenna

### 3.1. Four-Element Antenna Configuration

An initial configuration of the array is proposed by replicating and rotating the antenna element described inSection 2. As shown in Figure 5, the element pairs (1, 4) and (2, 3) provide spatial diversity, whereas the orthogonal arrangement of the pairs (1, 2) and (1, 3) results in polarization diversity. Good isolation was achieved by exploiting the spatial and polarization diversities. The ground planes of the antenna elements were separated by distance g=2mm to further improve the isolation. The dimensions of the MIMO antenna are 82 × 82 mm.Figure 5
Geometry of the MIMO antenna. (a) Top view and (b) bottom view.
(a)(b)The simulated S-parameters of the four-element MIMO antenna are depicted in Figure6. Owing to the symmetrical arrangement, |S12| = |S42| = |S34| = |S13| and |S14| = |S23|; therefore, only |S11|, |S12|, |S13|, and |S14| are presented here. S11 demonstrated that the antenna resonated at 4.46 and 5.38 GHz, which are the same resonance frequencies as those of the element in Figure 3. The minimum isolation levels were better than 25 dB in both bands.Figure 6
Simulated S-parameters of the four-element dual-band MIMO antenna.


### 3.2. Isolation Enhancement of the Four-Element Array

As shown in Figure7, four SNLs were inserted between the radiators of the MIMO antenna to further reduce the coupling current without increasing the size of the original MIMO antenna. The SNLs created additional current paths to transfer some of the current from one element and feed it back to another element with a suitable magnitude and an opposite phase, which eliminates the coupling. Each SNL was placed away from the open end of the antenna element in a low impedance area, where the current has the highest intensity. The decoupling current can be controlled by adjusting the location of the SNLs. Figure 8 shows the effects of location dnl on the isolation. Isolation higher than 35 dB in both bands was achieved when the location dnl was 5 mm.Figure 7
Geometry of the MIMO antenna with SNLs. (a) Top view and (b) bottom view.
(a)(b)Figure 8
Simulated S12 and S14 of the MIMO antenna with variations indnl.To further understand the contribution of the SNLs to isolation enhancement, the simulated current distributions with and without SNLs at 4.46 and 5.38 GHz are illustrated in Figure9. The current intensity in the other elements (2, 3, and 4) is reduced when element 1 is excited and the SNLs are introduced. Figure 9 shows that the SNLs are more effective in the lower band than in the upper band.Figure 9
Current distribution when element 1 is excited and other elements are terminated to match loads. (a) 4.46 GHz, without SNLs. (b) 4.46 GHz, with SNLs. (c) 5.38 GHz, without SNLs. (d) 5.38 GHz, with SNLs.
(a)(b)(c)(d)Figure10 presents the simulated S-parameters of the 2 × 2 MIMO antenna with the SNLs structure. The two simulated resonances appear at 4.46 and 5.38 GHz and the isolation in both bands is higher than 35 dB. This means the isolation in both bands increased by around 10 dB in comparison with the MIMO antenna without SNLs.Figure 10
Simulated S-parameters of MIMO antenna with SNLs.


## 3.1. Four-Element Antenna Configuration

An initial configuration of the array is proposed by replicating and rotating the antenna element described inSection 2. As shown in Figure 5, the element pairs (1, 4) and (2, 3) provide spatial diversity, whereas the orthogonal arrangement of the pairs (1, 2) and (1, 3) results in polarization diversity. Good isolation was achieved by exploiting the spatial and polarization diversities. The ground planes of the antenna elements were separated by distance g=2mm to further improve the isolation. The dimensions of the MIMO antenna are 82 × 82 mm.Figure 5
Geometry of the MIMO antenna. (a) Top view and (b) bottom view.
(a)(b)The simulated S-parameters of the four-element MIMO antenna are depicted in Figure6. Owing to the symmetrical arrangement, |S12| = |S42| = |S34| = |S13| and |S14| = |S23|; therefore, only |S11|, |S12|, |S13|, and |S14| are presented here. S11 demonstrated that the antenna resonated at 4.46 and 5.38 GHz, which are the same resonance frequencies as those of the element in Figure 3. The minimum isolation levels were better than 25 dB in both bands.Figure 6
Simulated S-parameters of the four-element dual-band MIMO antenna.


## 3.2. Isolation Enhancement of the Four-Element Array

As shown in Figure7, four SNLs were inserted between the radiators of the MIMO antenna to further reduce the coupling current without increasing the size of the original MIMO antenna. The SNLs created additional current paths to transfer some of the current from one element and feed it back to another element with a suitable magnitude and an opposite phase, which eliminates the coupling. Each SNL was placed away from the open end of the antenna element in a low impedance area, where the current has the highest intensity. The decoupling current can be controlled by adjusting the location of the SNLs. Figure 8 shows the effects of location dnl on the isolation. Isolation higher than 35 dB in both bands was achieved when the location dnl was 5 mm.Figure 7
Geometry of the MIMO antenna with SNLs. (a) Top view and (b) bottom view.
(a)(b)Figure 8
Simulated S12 and S14 of the MIMO antenna with variations indnl.To further understand the contribution of the SNLs to isolation enhancement, the simulated current distributions with and without SNLs at 4.46 and 5.38 GHz are illustrated in Figure9. The current intensity in the other elements (2, 3, and 4) is reduced when element 1 is excited and the SNLs are introduced. Figure 9 shows that the SNLs are more effective in the lower band than in the upper band.Figure 9
Current distribution when element 1 is excited and other elements are terminated to match loads. (a) 4.46 GHz, without SNLs. (b) 4.46 GHz, with SNLs. (c) 5.38 GHz, without SNLs. (d) 5.38 GHz, with SNLs.
(a)(b)(c)(d)Figure10 presents the simulated S-parameters of the 2 × 2 MIMO antenna with the SNLs structure. The two simulated resonances appear at 4.46 and 5.38 GHz and the isolation in both bands is higher than 35 dB. This means the isolation in both bands increased by around 10 dB in comparison with the MIMO antenna without SNLs.Figure 10
Simulated S-parameters of MIMO antenna with SNLs.


## 4. Fabrication and Measurement

As shown in Figure11, a prototype of the proposed MIMO antenna was fabricated to verify its effectiveness.Figure 11
Photograph of the fabricated MIMO antenna with SNLs. (a) Top view and (b) bottom view.
(a)(b)


### 4.1. S-Parameters

An Agilent N5227A vector network analyzer was used to measure the S-parameters. As shown in Figure12, the measured S11 resonated at 4.43 and 5.39 GHz. The measured minimum isolation levels in both bands are higher than 35 dB. These results are in good agreement with the simulation results.Figure 12
Measured S-parameters of the MIMO antenna with SNLs.


### 4.2. Radiation Patterns

The radiation patterns of the fabricated antenna were measured in an anechoic chamber and compared with the simulation results. Owing to the symmetry of the antenna structure, only the radiation patterns of element 1 are shown. As shown in Figure13, the simulated and measured radiation patterns at 4.46 and 5.38 GHz are in good agreement. The measured gains are 6 and 6.4 dBi, respectively, and the cross-polarization levels are lower than −14 dB in both bands. These results are in good agreement with the simulation results.Figure 13
Simulated and measured radiation patterns of the proposed MIMO antenna with SNLs. (a) 4.46 GHz, E-plane (xz-plane). (b) 4.46 GHz, H-plane (yz-plane). (c) 5.38 GHz, E-plane (xz-plane). (d) 5.38 GHz, H-plane (yz-plane).
(a)(b)(c)(d)


### 4.3. Diversity Performance

The diversity performance of the proposed MIMO antenna is described in terms of envelope correlation coefficient (ECC), diversity gain (DG), total active reflection coefficient (TARC), mean effective gain (MEG), and channel capacity loss (CCL).ECC is considered a paramount factor in the analysis of MIMO antennas. For better performance of the MIMO antenna, ECC < 0.5 across the operating frequency is essential. The ECC can be computed by using either the S-parameters [15] or three-dimensional far fields [12]:(1)ECC=ρij=Sii∗Sij+Sij∗Sjj21−Sii2−Sji21−Sjj2−Sij2,ECC=ρij=∬4πFiθ,φ⋅Fj∗θ,φdΩ2∬4πFiθ,φ2dΩ∬4πFjθ,φ2dΩ,where Fi (θ, φ) is a complex vector demonstrating the field radiating from the ith element. The symbols “⋅” and “∗” indicate the Hermitian product and the complex conjugate, respectively. In this paper, the ECC is computed using both methods. For brevity, only ρ12 and ρ14 are presented here. As shown in Figures 14 and 15, the computed ECC is less than 0.005 across the two operating bands, which satisfies the requirement ECC < 0.5 and indicates good system performance. The 3D far-field method for finding ECC gives more accurate results [17].Figure 14
Computed ECC of the proposed MIMO antenna using S-parameters.Figure 15
Computed ECC of the proposed MIMO antenna using three-dimensional far fields.DG determines the enhancement achieved by using multiple antenna systems over using single antenna systems. The relationship between ECC and DG can be described as [12](2)DG=101−0.99ρij2.It can be noted from (2) that a low ECC leads to ensure high DG. In an ideal case (ρij = 0), the DG is equal to 10 dB. As shown in Figure 16, the computed DG for the highest ECC values in the lower and upper operating bands is greater than 9.99 dB which guarantees good diversity performance.Figure 16
Computed diversity gain (DG) of the proposed MIMO antenna.TARC is the ratio of the square root of total reflected power divided by the square root of the total incident power. It can be computed using the following relation [18]:(3)Γat=∑i=1Nbi2∑i=1Nai2,where bi and ai represent reflected and incident signals, respectively, and N is the number of antenna elements. The computed TARC is shown in Figure 17. As can be seen, the TARC is better than –10 dB across the two operating bands.Figure 17
Computed total active reflection coefficient (TARC) of the proposed MIMO antenna.MEG is defined as the ratio of the mean received power to the mean incident power of the antenna. If the antennas are 100% efficient, the maximum MEG is –3 dB [19]. It can be computed using the following equation [20]:(4)MEG=12π∫02πΓ1+Γ⋅Gθπ2,ϕ+11+Γ⋅Gϕπ2,ϕdϕ,where Gθ and Gφ are, respectively, θ and φ polarized components of the antenna power gain pattern. Г is the cross-polarization discrimination of the incident field. The ratios of the MEG should satisfy the following condition in order to guarantee good channel characteristics [21]:(5)MEGiMEGj≅1.In our design, average MEG of –3.2 dB is achieved for all the four elements. The ratios of MEGi/MEGj are around 0.937 which satisfies condition (5).CCL caused by the correlation can be expressed as [22](6)Closs=−log2detΨR,where ΨR is the correlation matrix. Figure 18 shows that the proposed MIMO antenna achieves lower than 0.2 CCL values (ideally, CCL should be < 0.4 bits/s/Hz) across the two operating bands. We can conclude that the diversity performances of the proposed MIMO antenna are suitable for a high-quality MIMO antenna system.Figure 18
Computed channel capacity loss (CCL) of the proposed MIMO antenna.The performance of the proposed MIMO antenna is compared with that of the recent four-element MIMO antenna in Table1. Our 2 × 2 MIMO antenna has the highest isolation and gain. The proposed antenna also has the smallest edge-to-edge element spacing. The size of this work is smaller than that of the antenna in [14] and approximately equal to antenna in [15] and larger than that of the antennas in [11–13]. Our design has the smallest envelope correlation coefficient which guarantees good diversity performance. In this design, we used the coaxial probes to excite the dual-band antenna elements. In summary, our proposed 2 × 2 MIMO antenna has the highest isolation, highest gain, smallest edge-to-edge element spacing, and lowest envelope correlation coefficient.Table 1
Comparison study.
ReferenceCenter frequency (GHz)Edge-to-edge (λ0)Gain (dBi)Minimum isolation (dB)Total sizeDiversity performance ECCExcitation[11]2.45, 5.500.30NA17.50.9λ0 × 0.9 λ0 × 0.015 λ00.057Coaxial probe[12]3.50, 5.700.0382.7, 2.818.40.7λ0 × 0.7 λ0 × 0.075 λ00.08Microstrip line[13]2.93, 5.680.2264.0, 4.0140.8λ0 × 0.8 λ0 × 0.031 λ00.05Microstrip line[14]3.27, 5.400.4474.8, 5.3201.6λ0 × 1.6 λ0 × 0.236 λ00.06Aperture coupled[15]2.54, 5.260.2953.9, 4.1211.3λ0 × 1.3 λ0 × 0.027 λ00.07Microstrip lineThis work4.43, 5.390.0366, 6.4351.4λ0 × 1.4 λ0 × 0.028 λ00.005Coaxial probeλ0 is the free-space wavelength at the upper-frequency band. NA = not available.


## 4.1. S-Parameters

An Agilent N5227A vector network analyzer was used to measure the S-parameters. As shown in Figure12, the measured S11 resonated at 4.43 and 5.39 GHz. The measured minimum isolation levels in both bands are higher than 35 dB. These results are in good agreement with the simulation results.Figure 12
Measured S-parameters of the MIMO antenna with SNLs.


## 4.2. Radiation Patterns

The radiation patterns of the fabricated antenna were measured in an anechoic chamber and compared with the simulation results. Owing to the symmetry of the antenna structure, only the radiation patterns of element 1 are shown. As shown in Figure13, the simulated and measured radiation patterns at 4.46 and 5.38 GHz are in good agreement. The measured gains are 6 and 6.4 dBi, respectively, and the cross-polarization levels are lower than −14 dB in both bands. These results are in good agreement with the simulation results.Figure 13
Simulated and measured radiation patterns of the proposed MIMO antenna with SNLs. (a) 4.46 GHz, E-plane (xz-plane). (b) 4.46 GHz, H-plane (yz-plane). (c) 5.38 GHz, E-plane (xz-plane). (d) 5.38 GHz, H-plane (yz-plane).
(a)(b)(c)(d)


## 4.3. Diversity Performance

The diversity performance of the proposed MIMO antenna is described in terms of envelope correlation coefficient (ECC), diversity gain (DG), total active reflection coefficient (TARC), mean effective gain (MEG), and channel capacity loss (CCL).ECC is considered a paramount factor in the analysis of MIMO antennas. For better performance of the MIMO antenna, ECC < 0.5 across the operating frequency is essential. The ECC can be computed by using either the S-parameters [15] or three-dimensional far fields [12]:(1)ECC=ρij=Sii∗Sij+Sij∗Sjj21−Sii2−Sji21−Sjj2−Sij2,ECC=ρij=∬4πFiθ,φ⋅Fj∗θ,φdΩ2∬4πFiθ,φ2dΩ∬4πFjθ,φ2dΩ,where Fi (θ, φ) is a complex vector demonstrating the field radiating from the ith element. The symbols “⋅” and “∗” indicate the Hermitian product and the complex conjugate, respectively. In this paper, the ECC is computed using both methods. For brevity, only ρ12 and ρ14 are presented here. As shown in Figures 14 and 15, the computed ECC is less than 0.005 across the two operating bands, which satisfies the requirement ECC < 0.5 and indicates good system performance. The 3D far-field method for finding ECC gives more accurate results [17].Figure 14
Computed ECC of the proposed MIMO antenna using S-parameters.Figure 15
Computed ECC of the proposed MIMO antenna using three-dimensional far fields.DG determines the enhancement achieved by using multiple antenna systems over using single antenna systems. The relationship between ECC and DG can be described as [12](2)DG=101−0.99ρij2.It can be noted from (2) that a low ECC leads to ensure high DG. In an ideal case (ρij = 0), the DG is equal to 10 dB. As shown in Figure 16, the computed DG for the highest ECC values in the lower and upper operating bands is greater than 9.99 dB which guarantees good diversity performance.Figure 16
Computed diversity gain (DG) of the proposed MIMO antenna.TARC is the ratio of the square root of total reflected power divided by the square root of the total incident power. It can be computed using the following relation [18]:(3)Γat=∑i=1Nbi2∑i=1Nai2,where bi and ai represent reflected and incident signals, respectively, and N is the number of antenna elements. The computed TARC is shown in Figure 17. As can be seen, the TARC is better than –10 dB across the two operating bands.Figure 17
Computed total active reflection coefficient (TARC) of the proposed MIMO antenna.MEG is defined as the ratio of the mean received power to the mean incident power of the antenna. If the antennas are 100% efficient, the maximum MEG is –3 dB [19]. It can be computed using the following equation [20]:(4)MEG=12π∫02πΓ1+Γ⋅Gθπ2,ϕ+11+Γ⋅Gϕπ2,ϕdϕ,where Gθ and Gφ are, respectively, θ and φ polarized components of the antenna power gain pattern. Г is the cross-polarization discrimination of the incident field. The ratios of the MEG should satisfy the following condition in order to guarantee good channel characteristics [21]:(5)MEGiMEGj≅1.In our design, average MEG of –3.2 dB is achieved for all the four elements. The ratios of MEGi/MEGj are around 0.937 which satisfies condition (5).CCL caused by the correlation can be expressed as [22](6)Closs=−log2detΨR,where ΨR is the correlation matrix. Figure 18 shows that the proposed MIMO antenna achieves lower than 0.2 CCL values (ideally, CCL should be < 0.4 bits/s/Hz) across the two operating bands. We can conclude that the diversity performances of the proposed MIMO antenna are suitable for a high-quality MIMO antenna system.Figure 18
Computed channel capacity loss (CCL) of the proposed MIMO antenna.The performance of the proposed MIMO antenna is compared with that of the recent four-element MIMO antenna in Table1. Our 2 × 2 MIMO antenna has the highest isolation and gain. The proposed antenna also has the smallest edge-to-edge element spacing. The size of this work is smaller than that of the antenna in [14] and approximately equal to antenna in [15] and larger than that of the antennas in [11–13]. Our design has the smallest envelope correlation coefficient which guarantees good diversity performance. In this design, we used the coaxial probes to excite the dual-band antenna elements. In summary, our proposed 2 × 2 MIMO antenna has the highest isolation, highest gain, smallest edge-to-edge element spacing, and lowest envelope correlation coefficient.Table 1
Comparison study.
ReferenceCenter frequency (GHz)Edge-to-edge (λ0)Gain (dBi)Minimum isolation (dB)Total sizeDiversity performance ECCExcitation[11]2.45, 5.500.30NA17.50.9λ0 × 0.9 λ0 × 0.015 λ00.057Coaxial probe[12]3.50, 5.700.0382.7, 2.818.40.7λ0 × 0.7 λ0 × 0.075 λ00.08Microstrip line[13]2.93, 5.680.2264.0, 4.0140.8λ0 × 0.8 λ0 × 0.031 λ00.05Microstrip line[14]3.27, 5.400.4474.8, 5.3201.6λ0 × 1.6 λ0 × 0.236 λ00.06Aperture coupled[15]2.54, 5.260.2953.9, 4.1211.3λ0 × 1.3 λ0 × 0.027 λ00.07Microstrip lineThis work4.43, 5.390.0366, 6.4351.4λ0 × 1.4 λ0 × 0.028 λ00.005Coaxial probeλ0 is the free-space wavelength at the upper-frequency band. NA = not available.


## 5. Conclusion

In this paper, a close-spaced dual-band 2 × 2 MIMO antenna is proposed and fabricated. Good isolation was achieved by exploiting spatial and polarization diversities. An isolation enhancement of around 10 dB was achieved by inserting SNLs at the center of the MIMO antenna between the radiators of the antenna elements without increasing the size of the original MIMO antenna. With only 0.036λ0 edge-to-edge distance between elements, the measured isolation in both bands was higher than 35 dB. Moreover, the diversity performances of the proposed MIMO antenna are suitable for a high-quality MIMO antenna system.



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*Source: 2965767-2020-11-27.xml*