# Robust Finite-Time H-Infinity Control with Transients for Dynamic Positioning Ship Subject to Input Delay

Authors: Xiaogong Lin; Kun Liang; Heng Li; Yuzhao Jiao; Jun Nie
Journal: Mathematical Problems in Engineering
 (2018)

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## Abstract

This paper presents the problem of robust finite-timeH∞ control with transients for ocean surface vessels equipped with dynamic positioning (DP) system in presence of input delay. The main objective of this work is to design a finite-time H∞ state feedback controller, which ensures that all states of ship do not exceed a given threshold over a fixed time interval, with better robustness and transient performance subject to time-varying disturbance. Based on a novel augmented Lyapunov-Krasovskii-like function (LKLF) with triple integral terms and a method combining the Wirtinger inequality and reciprocally convex approach, a less conservative result is derived. In particular, an H∞ performance index with nonzero initial condition is introduced to attenuate the overconservatism caused by the assumption of zero initial condition and enhance the transient performance of ship subject to external disturbance. More precisely, the controller gain matrix for the DP system can be achieved by solving the linear matrix inequalities (LMIs), which can be easily facilitated by using some standard numerical packages. Finally, a numerical simulation for a ship is proposed to verify the effectiveness and less conservatism of the controller we designed.


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## Body

## 1. Introductions

With the increasing development in the ocean exploitation, dynamic positioning (DP) systems, regulating the horizontal position and heading of the vessel exclusively by means of active thrusters, have been developed for various marine and offshore applications such as drilling, salvage, pipe-laying, and oil production [1]. To achieve expected trajectory tracking or positioning, various control strategies have been proposed, including robust adaptive control [2], sliding mode control [3], prescribed performance control [4], hybrid control [5], and neural network control [6]. However, in some applications, it is significant to maintain the vessel’s states under some bounds, particularly of which transient performance is emphasized, during a specific time interval, for example, when facing the matter of saturations or when the task of trajectory tracking should be fulfilled in a prescribed time interval. In [7], the proposed controller can maintain the bound of ship over an infinity time interval regardless of disturbance. However, it is inconvenient to analyze and to enhance the transient performance when the operation should be arrived in short time, such as rescuing works. On the other hand, time delay is encountered in many dynamical systems and often leads to performance deterioration which engenders strongly growing interest in this topic in recent decades. In the DP system, the main kind of time delay is encountered in actuators [8], while another obvious kind of delay is the one produced between the sensors and the activation of the control mechanism [9]. The effect caused by time delay will be more significant in finite-time interval and it is the first motivation of this paper.The classicalH∞ control theory [10] defines the control law, under the assumption of zero initial condition, providing the minimal value to the performance measure that is the worst-case norm of the regulated output over all exogenous signals and is applied to DP system successfully [11]. However, there exist some situations, when the initial state of ship is possibly nonzero, such as when saturation is activated or controller is switched to another one. It will cause an additional unknown disturbance [12] and the promising robustness is achieved at the expense of degraded nominal performance [13]. In [14], researchers introduced a performance measure that is the induced norm of the regulated output over all exogenous signals and initial states for finite and infinite horizons. Unfortunately, to the best the authors’ knowledge, it has not been extended to the system with input delay. On another research frontier, various approaches, in the framework of finite-time boundedness for time-delay systems, have been developed to obtain the results with less conservatism [15, 16], usually indicated by the bound of state [17]. For DP system, engineers are willing to obtain control strategies which maintain the state of ship varying in a small region around the desired set-point or tracking path instead of the acceptable minimum state bound. Thus, the second motivate is to obtain a result which reduces the overconservatism caused by the assumption of zero initial condition and the loss information in the proof for time delay systems in a practical view.Based on the discussion aforementioned, the problem of robust finite-timeH∞ control for DP system with input delay is studied. The main contribution of this paper lies in three aspects: Firstly, a finite-time H∞ controller with transients is designed for DP systems with input delay, by solving a couple of LMIs, which can guarantee the state of ship within a desired value over a fixed time interval in the presence of time-varying disturbances. Secondly, the concept of H∞ control under nonzero initial condition is introduced to time-delay system and its advantage on enhancing the transient performance will be shown in a numerical simulation compared to the H∞ with zero initial condition. In particular, the results are established in forms of LMI, which can be easily facilitated by using some standard numerical packages. Thirdly, a novel augmented LKLF with triple integral terms, which contains more information is constructed; meanwhile a method combining the Wirtinger inequality and reciprocally convex approach is applied to obtain a tight bound of the integral terms of quadratic functions which may lead to a less conservative result compared to previous works. Moreover, the practical significance of this method in engineering will be demonstrated later. Finally, a numerical simulation for a ship is proposed to verify the effectiveness and advantage of the controller we designed.The rest of this paper is organized as follows: In Section2, the problem formulation of finite-time H∞ control is detailed for vessels while some definitions and lemmas are introduced as preparation. In Section 3, the method to design finite-time H∞ controller is proposed, and the proposed control schemes are simulated in Section 4. In Section 5, the conclusion is drawn.Notation. Throughout this paper, Rn is the n-dimensional Euclidean vector space, and Rm×n denotes the set of all m×n real matrices. For symmetric matrices X and Y, X>Y (respectively, X≥Y ) means that X-Y is positive definite (respectively, positive semidefinite). The superscript “T” represents the transpose. The symmetric terms in a symmetric matrix are denoted by “∗”. Moreover, we use λmax·(λmin· ) to denote the maximum (minimum) eigenvalue of a symmetric matrix.


## 2. Problem Formulation

### 2.1. Model of DP System

At first, DP system model with three-DOP under low speed can be described as [18](1)η˙t=Jψυt(2)Mυ˙t+Dυt=ut-ht+ωtwhere υ=μvr is a vector of velocities given in the body-fixed coordinate system and η=XYψ is the position and orientation of the vessel with respect to an inertial reference coordinate system. ut is a control vector of forces and moments provided by the propulsion systems. ht is a time-varying function that expresses the actuator delay and satisfies ht<hh˙t<μ  . ωt is the disturbance input of the system and satisfies the condition of ∫0∞ωtTωtdt<d  . Jψ is the transformation matrix between the inertial and body-fixed coordinate frames. The inertia matrix M includes hydrodynamic added inertia, and D is a strictly positive damping matrix due to linear wave drift damping and laminar friction. Then, the structures of the matrices Jψ, M, and D can be explicitly given as follows:(3)Jψ=cosψ-sinψ0sinψcosψ0001M=m-Xu˙000m-Yv˙mxg-Yr˙0mxg-Yr˙Iz-Nr˙D=-Xu000YvYr0NvNrwhereXu  ,Yv  ,Yr  ,Nr  ,Xu˙  ,Yv˙  ,Yr˙, and Nr˙ are the hydrodynamic parameters of the vessel. m is the mass of the ship, and Iz is the moment of inertia about the yaw rotation. xg is the vertical distance from coordinate origin to center of gravity in body-fixed frame.To simplify the model, some assumptions are introduced first.Assumption 1.
All the parameters of state are available.Assumption 2.
The roll and pitch angles are small enough; for DP system, it is a reasonable assumption.Under assumption 2, we can obtain the simplified equation in form of state-space [19](4)x˙t=Axt+B1ut-ht+B2ωt(5)zt=Cxt+Dut-htwhere(6)xt=ηtυtA=0I0-M-1DB1=B2=0M-1.Under assumption 1, we design the full-state feedback as(7)ut-ht=Kxt-htso the (1) and (2) can be rewritten as(8)x˙t=Axt+B1Kxt-ht+B2ωt(9)zt=Cxt+DKxt-ht.Remark 3.
In the situation of DP motion, the motion in heave, roll, and pitch will be ignored since we focus on the motion on the surface of sea. Meanwhile, velocity of vessel is low enough, so the Coriolis-Centripetal matrix and nonlinearities in damping matrix can be neglected [18].Remark 4.
In measurement subsystem of DP system, various sensors are installed to obtain the state of the vessel motion accurately, including global position system for the vessel’ s position, gyrocompass for the vessel’ s heading, and attitude sensor for the pitch and roll. Meanwhile, data fusion technology is applied to DP system to obtain more accurate state information of vessel motion [18].


### 2.2. Preliminaries

In the sequel, some definitions and lemmas are introduced to obtain the results.Definition 5 ((FTB), see [20]).
Given a positive definite matrixR and three positive constants c1, c2, T with c1<c2, the time-delay system (4) with ut=0 is said to be finite-time boundedness with respect to c1c2dTτR, if sup-τ<θ<0xTθRxθ,x˙TθRx˙θ<c1⇒xTtRxt<c2, ∀t∈0,T, ∀ωt: ∫0TωtTωtdt<d.Definition 6.
Givenγ>0, time-delay systems (4) and (5) are said to be H∞- FTB under nonzero initial condition (H∞- FTB) with c1c2dγTτR, if the following conditions are satisfied:
(1) time-delay system (4) with ut=0 is FTB;
(2) under the initial condition thatx0≠0, output zt satisfies(10)Γ=supωt2,0,T2+x0TSx0≠0⁡zt2,0,T2ωt2,0,T2+x0TSx01/2<γwhere γ is a prescribed scalar and S is a weighting diagonal matrix that penalizes the effect caused by the initial state.Remark 7.
It is necessary to distinguish between finite-time stability and finite-time attractiveness [21]. The first concept is to maintain system states within a given boundary in a specified time interval [22, 23], while the latter describes the fact that system state reaches the equilibrium point of system in a finite time [24].Remark 8.
Similar to [13], this definition of H∞ performance, which depends on the initial condition, has been extended to linear system with acceptable maximal delay bound. The performance measure is parametrised by a weighting matrix S reflecting the relative importance of the uncertainty in the initial state contrary to the uncertainty in the exogenous disturbance. When S=0, it will reduce into a sort of H∞ control with zero initial condition [25–27].Lemma 9 (see [28]).
For any matrixP>0 and a differentiable signal x in -a,-b→Rn, the following inequality holds:(11)∫-a-bx˙TuS1x˙uds≥1a-bΠ1S1,xT-b,xT-a,1a-b∫-a-bxTuduwhere(12)Π1S1,α,β,γ=α-βTα+β-2γTTS10∗3S1α-βTα+β-2γT.Lemma 10 (see [29]).
For constant matricesS1>0, S2>0 and constant scalars a>b, the following inequalities hold for all continuously function x in -a,-b→Rn:(13)∫-a-b∫t+θt-bx˙TuS2x˙ududθ≥Π2S2,xTt-b,1a-b∫t-at-bxTudu,1a-b2∫-a-b∫t+θt-bxTududθ∫-a-b∫t-at+θx˙TuS3x˙ududθ≥Π3S3,xTt-a,1a-b∫t-at-bxTudu,1a-b2∫-a-b∫t+θt-bxTududθwhere(14)Π2S2,α,β,γ=α-βTα2-γTT6S2-12S2∗36S2α-βTα2-γTΠ3S3,α,β,γ=α-βTα2-β+γTT6S3-12S3∗36S3α-βTα2-β+γT.Lemma 11 (see [30]).
Letf1,f2,…,fN: Rm↦R have positive values in an open subset D of Rm. Then the reciprocally convex combination of fi over D satisfies(15)minαi∣αi>0,∑iαi=1∑i1αifit=∑ifit+maxgi,jt⁡∑i≠jgi,jtsubjecttogi,j:Rm⟼R,gj,it=gi,jt,fitgi,jtgj,itfjt≥0.Lemma 12 (see [31]).
For any matrixS4>0 and a vector function x in -a,-b→Rn, if the integrals concerned are well defined, then the following inequality holds:(16)∫-a-bxTsS4xsds≥1a-b∫-a-bxTsdsS4∫-a-bxsds.


### 2.3. Control Objective

Finally, the objective of this paper is to derive the control gainK such that(1)
the closed-loop system (8) with ut=0 is FTB;(2)
under given nonzero initial condition, the closed system (8) and (9) guarantees that J=∫0TzTszs-γ2ωTsωs-γ21/TxT0Sx0ds<0 for all nonzero ωt and t∈0,T.


## 2.1. Model of DP System

At first, DP system model with three-DOP under low speed can be described as [18](1)η˙t=Jψυt(2)Mυ˙t+Dυt=ut-ht+ωtwhere υ=μvr is a vector of velocities given in the body-fixed coordinate system and η=XYψ is the position and orientation of the vessel with respect to an inertial reference coordinate system. ut is a control vector of forces and moments provided by the propulsion systems. ht is a time-varying function that expresses the actuator delay and satisfies ht<hh˙t<μ  . ωt is the disturbance input of the system and satisfies the condition of ∫0∞ωtTωtdt<d  . Jψ is the transformation matrix between the inertial and body-fixed coordinate frames. The inertia matrix M includes hydrodynamic added inertia, and D is a strictly positive damping matrix due to linear wave drift damping and laminar friction. Then, the structures of the matrices Jψ, M, and D can be explicitly given as follows:(3)Jψ=cosψ-sinψ0sinψcosψ0001M=m-Xu˙000m-Yv˙mxg-Yr˙0mxg-Yr˙Iz-Nr˙D=-Xu000YvYr0NvNrwhereXu  ,Yv  ,Yr  ,Nr  ,Xu˙  ,Yv˙  ,Yr˙, and Nr˙ are the hydrodynamic parameters of the vessel. m is the mass of the ship, and Iz is the moment of inertia about the yaw rotation. xg is the vertical distance from coordinate origin to center of gravity in body-fixed frame.To simplify the model, some assumptions are introduced first.Assumption 1.
All the parameters of state are available.Assumption 2.
The roll and pitch angles are small enough; for DP system, it is a reasonable assumption.Under assumption 2, we can obtain the simplified equation in form of state-space [19](4)x˙t=Axt+B1ut-ht+B2ωt(5)zt=Cxt+Dut-htwhere(6)xt=ηtυtA=0I0-M-1DB1=B2=0M-1.Under assumption 1, we design the full-state feedback as(7)ut-ht=Kxt-htso the (1) and (2) can be rewritten as(8)x˙t=Axt+B1Kxt-ht+B2ωt(9)zt=Cxt+DKxt-ht.Remark 3.
In the situation of DP motion, the motion in heave, roll, and pitch will be ignored since we focus on the motion on the surface of sea. Meanwhile, velocity of vessel is low enough, so the Coriolis-Centripetal matrix and nonlinearities in damping matrix can be neglected [18].Remark 4.
In measurement subsystem of DP system, various sensors are installed to obtain the state of the vessel motion accurately, including global position system for the vessel’ s position, gyrocompass for the vessel’ s heading, and attitude sensor for the pitch and roll. Meanwhile, data fusion technology is applied to DP system to obtain more accurate state information of vessel motion [18].


## 2.2. Preliminaries

In the sequel, some definitions and lemmas are introduced to obtain the results.Definition 5 ((FTB), see [20]).
Given a positive definite matrixR and three positive constants c1, c2, T with c1<c2, the time-delay system (4) with ut=0 is said to be finite-time boundedness with respect to c1c2dTτR, if sup-τ<θ<0xTθRxθ,x˙TθRx˙θ<c1⇒xTtRxt<c2, ∀t∈0,T, ∀ωt: ∫0TωtTωtdt<d.Definition 6.
Givenγ>0, time-delay systems (4) and (5) are said to be H∞- FTB under nonzero initial condition (H∞- FTB) with c1c2dγTτR, if the following conditions are satisfied:
(1) time-delay system (4) with ut=0 is FTB;
(2) under the initial condition thatx0≠0, output zt satisfies(10)Γ=supωt2,0,T2+x0TSx0≠0⁡zt2,0,T2ωt2,0,T2+x0TSx01/2<γwhere γ is a prescribed scalar and S is a weighting diagonal matrix that penalizes the effect caused by the initial state.Remark 7.
It is necessary to distinguish between finite-time stability and finite-time attractiveness [21]. The first concept is to maintain system states within a given boundary in a specified time interval [22, 23], while the latter describes the fact that system state reaches the equilibrium point of system in a finite time [24].Remark 8.
Similar to [13], this definition of H∞ performance, which depends on the initial condition, has been extended to linear system with acceptable maximal delay bound. The performance measure is parametrised by a weighting matrix S reflecting the relative importance of the uncertainty in the initial state contrary to the uncertainty in the exogenous disturbance. When S=0, it will reduce into a sort of H∞ control with zero initial condition [25–27].Lemma 9 (see [28]).
For any matrixP>0 and a differentiable signal x in -a,-b→Rn, the following inequality holds:(11)∫-a-bx˙TuS1x˙uds≥1a-bΠ1S1,xT-b,xT-a,1a-b∫-a-bxTuduwhere(12)Π1S1,α,β,γ=α-βTα+β-2γTTS10∗3S1α-βTα+β-2γT.Lemma 10 (see [29]).
For constant matricesS1>0, S2>0 and constant scalars a>b, the following inequalities hold for all continuously function x in -a,-b→Rn:(13)∫-a-b∫t+θt-bx˙TuS2x˙ududθ≥Π2S2,xTt-b,1a-b∫t-at-bxTudu,1a-b2∫-a-b∫t+θt-bxTududθ∫-a-b∫t-at+θx˙TuS3x˙ududθ≥Π3S3,xTt-a,1a-b∫t-at-bxTudu,1a-b2∫-a-b∫t+θt-bxTududθwhere(14)Π2S2,α,β,γ=α-βTα2-γTT6S2-12S2∗36S2α-βTα2-γTΠ3S3,α,β,γ=α-βTα2-β+γTT6S3-12S3∗36S3α-βTα2-β+γT.Lemma 11 (see [30]).
Letf1,f2,…,fN: Rm↦R have positive values in an open subset D of Rm. Then the reciprocally convex combination of fi over D satisfies(15)minαi∣αi>0,∑iαi=1∑i1αifit=∑ifit+maxgi,jt⁡∑i≠jgi,jtsubjecttogi,j:Rm⟼R,gj,it=gi,jt,fitgi,jtgj,itfjt≥0.Lemma 12 (see [31]).
For any matrixS4>0 and a vector function x in -a,-b→Rn, if the integrals concerned are well defined, then the following inequality holds:(16)∫-a-bxTsS4xsds≥1a-b∫-a-bxTsdsS4∫-a-bxsds.


## 2.3. Control Objective

Finally, the objective of this paper is to derive the control gainK such that(1)
the closed-loop system (8) with ut=0 is FTB;(2)
under given nonzero initial condition, the closed system (8) and (9) guarantees that J=∫0TzTszs-γ2ωTsωs-γ21/TxT0Sx0ds<0 for all nonzero ωt and t∈0,T.


## 3. Main Results

The designing of the robust finite-timeH∞ controller for the DP system with input delay is divided into three steps.


### 3.1. FTB Analysis of DP System

Firstly, the result guaranteeing the FTB of DP system is established in this subsection.Theorem 13.
Given five positive scalarsα, β, c1,c2,T and positive define matrix R, the finite-time boundedness problem of system (4) is solvable if there exist positive scalars θll=1,2,⋯,8 and matrices P11>0, P22>0, W>0, Qi>0i=1,2, Uj>0j=1,2, M>0, Z1, Z2 with appropriate dimensions, satisfying the following conditions:(17)Ω=Ωij8×8<0(18)WZ1∗W>0(19)3WZ2∗3W>0(20)c1θ2+h2c1θ3+ρhc1θ4+ρhc1θ5+12ρh3c1θ6+16ρh3c1θ7+13ρh3c1θ8+βθ9d<e-αTc2θ1where(21)Ω11=ATP11+P11A-αP11+Q1+Q2+AT12h2U1+U2+2WA-4ρW-3ρU1-9ρU2,Ω22=-ρQ2-4ρW-6ρU2,Ω33=KTB1T12h22W+U1+U2B1K-8ρW+ρZ1T+ρZ1-ρZ2T-ρZ2-1-μQ2,Ω44=B2T12h22W+U1+U2B2-βM,Ω66=-12ρW,Ω77=-12ρW,Ω55=αh2P22-18ρU2-6ρU1,Ω88=-36ρU1-36ρU2,Ω12=ρZ1-ρZ2+6ρU2,Ω15=hP22+12ρU2,Ω16=6ρW,Ω17=2ρZ2,Ω13=P11B1K+AT12h22W+U1+U2B1K-2ρW-ρZ1-ρZ2,Ω14=P11B2+AT12h22W+U1+U2B2,Ω18=-18ρU2+6ρU1,Ω23=-ρZ1T-ρZ2T-2ρW,Ω25=-hP22-6ρU2,Ω26=2ρZ2T,Ω27=6ρW,Ω28=12ρU2,Ω34=KTB1T12h22W+U1+U2B2,Ω36=6ρW+2ρZ2T,Ω37=6ρW+2ρZ2,Ω58=12ρU1+24ρU2,Ω67=-4ρZ2,Ω24=Ω35=Ω38=Ω45=Ω46=Ω47=Ω48=Ω56=Ω57=Ω68=Ω78=0,θ1=λminP~11θ2=λmaxP~11,θ3=λmaxP~22,θ4=λmaxQ~1,θ5=λmaxQ~2,θ6=λmaxW~,θ7=λmaxU~1,θ8=λmaxU~2,θ9=λmaxM,ρ=eαh,P~11=R-1/2P11R-1/2,P~22=R-1/2P22R-1/2,Q~i=R-1/2QiR-1/2i=1,2,3,W~=R-1/2WR-1/2,U~j=R-1/2UjR-1/2j=1,2,0<θ1I<P11<θ2I,0<P22<θ3I,0<Q1<θ4I,0<Q2<θ5I,0<W<θ6I,0<U1<θ7I,0<U2<θ8I,0<M<θ9I.Proof.
Consider the candidate augment LKLF as follows:(22)Vt=V1t+V2t+V3t+V4t(23)V1t=εtTPεt(24)V2t=∫t-hteαt-sxsTQ1xsds+∫t-htteαt-sxsTQ2xsds(25)V3t=h∫-h0∫t+θteαt-sx˙sTWx˙sdsdθ(26)V4t=∫-h0∫θ0∫t+βteαt-sx˙sTU1x˙sdsdβdθ+∫-h0∫-hθ∫t+βteαt-sx˙sTU2x˙sdsdβdθwhere εt=xt∫t-htxsdsP=P110∗P22.
To deal with the formulas conveniently, let us provide such definitions:(27)ξt=xtxt-hxt-htωt1h∫t-htxsds1ht∫t-httxsds1h-ht∫t-ht-htxsds1h2∫-h0∫t+θtxsdsdθlkT=0⋯0︸k-110⋯0︸8-k.
The time-derivative ofVt along system (4) can be bounded as (28)V˙1t=αV1t+ε˙tTPεt+εtTPε˙t-αV1t(29)V˙2t=αV2t+xtTQ1xt-eαhxt-hTQ1xt-h+xtTQ2xt-1-h˙teαhtxt-htTQ2xt-ht≤αV2t+xtTQ1xt-eαhxt-hTQ1xt-h+xtTQ2xt-1-μxt-htTQ2xt-ht(30)V˙3t=αV3t+h2x˙tTW2x˙t-eαhh∫t-htx˙sTW2x˙sds(31)V˙4t=αV4t+12h2x˙tTU1x˙t-eαh∫-h0∫t+βtx˙sTU1x˙sdsdβ+12h2x˙tTU2x˙t-eαh∫-h0∫t-ht+βx˙sTU2x˙sdsdβ.
Invoking Lemma9, we can obtain(32)V˙3t=αV3t+h2x˙tTWx˙t-eαhh∫t-httx˙sTWx˙sds-eαhh∫t-ht-htx˙sTWx˙sds≤αV3t+h2x˙tTWx˙t-eαhhhtϖ1TΛ1ϖ1-eαhhh-htϖ2TΛ2ϖ2where(33)ϖ1T=ξTtl1T-l3TTl1T+l3T-2l6TTTϖ2T=ξTtl3T-l2TTl3T+l2T-2l7TTΛ1=Λ2=W0∗3W.
In order to obtain a tighter bound of integral term, Lemma11 is applied to (32) as follows:(34)V˙3t≤αV3t+h2x˙tTWx˙t-eαhϖ3TΛ3ϖ3where ϖ3T=ϖ1Tϖ2T, Λ3=WZ100∗W00∗∗3WZ2∗∗∗3W.
By applying Lemma10 to (31), we can obtain the inequality(35)V˙4t≤αV4t+12h2x˙tTU1x˙t+12h2x˙tTU2x˙t-eαhϖ4TΛ4ϖ4where(36)ϖ4T=ξTtl1T-l2TT12l1T-l8TTl2T-l5TT12l2T-l5T+l8TTTΛ4=6U1-12U100∗36U100∗∗6U2-12U2∗∗∗36U2.
Combining (28), (29), (34), and (35) with the definition of ρ=eαh, we can obtain(37)V˙-αV-βωTtMωt<ξTtΩξt.
Assuming thatΩ<0 and integrating the left part of inequality (37),(38)Vt<eαtV0+β∫0teαt-sωTsMωsds<eαTV0+βλmaxMd.
Invoking the Jensen inequality shown in Lemma12, one has(39)V0≤x0TP11x0+h∫-h0xsTP22xsds+ρ∫-h0xsTQ1xsds+ρ∫-ht0xsTQ2xsds+hρ∫-h0∫θ0x˙sTWx˙sdsdθ+ρ∫-h0∫θ0∫β0x˙sTU1x˙sdsdβdθ+ρ∫-h0∫-hθ∫β0x˙sTU2x˙sdsdβdθ≤λmaxP~11c1+hλmaxP~22hc1+ρλmaxQ~1hc1+ρλmaxQ~2hc1+ρλmaxW~12h3c1+ρλmaxU~116h3c1+ρλmaxU~213h3c1
Based on inequalities (38) and (39), we have(40)Vt>xTtP11xt=xTtR1/2P~11R1/2xt>λminP~11xTtRxt.
Therefore, conditions (17) to (20) can guarantee the FTB of system (4). This completes the proof.Remark 14.
Among the existing approaches, there are two threads: one is to construct a novel LKLF that involves more information of delay; the other is to find a tighter estimation of upper bound for cross terms coming from the derivative of the LKLF. In this paper, these two techniques are applied to obtain the result. In addition, the less conservatism in practical engineering will be shown in the simulations which are always ignored in most literature sources.


### 3.2. Controller Design

In this subsection, we focus on the problem of finite-timeH∞ state feedback designing based on Theorem 13, that is, designing a state feedback controller in the form of (7) such that the resulting DP system satisfies the control objective proposed in Section 1.Theorem 15.
For given positiveα, c1, c2, T, γ and matrices R>0, S≥0, if there exist positive scalars θll=1,2,⋯,8 and matrices P-11>0, P-22>0, W->0, Q-i>0i=1,2, U-j>0j=1,2, Y,Z-1,Z-2 with appropriate dimensions, satisfying the following conditions:(41)Π~=Π~ij12×12<0(42)Σ=Σij9×9<0(43)W-Z-1∗W->0(44)3W-Z-2∗3W->0(45)I-γ2SP-11<0(46)0<H1<P-11<H2,0<P-22<H3,0<Q-1<H4,0<Q-2<H5,0<W-<H6,0<U-1<H7,0<U-2<H8,where(47)Π~11=P-11AT+AP-11-αP-11+Q-1+Q-2-4ρW--3ρU-1-9ρU-2,Π~44=-γ2I,Π~22=-ρQ-2-4ρW--6ρU-2,Π~33=-8ρW-+ρZ-1T+ρZ-1-ρZ-2T-ρZ-2-1-μQ-2,Π~13=B1Y-2ρW--ρZ-1-ρZ-2,Π~14=B2,Π~66=-12ρW-,Π~77=-12ρW-,Π~55=αh2P-22-18ρU-2-6ρU-1,Π~88=-36ρU-1-36ρU-2,Π~12=ρZ-1-ρZ-2+6ρU-2,Π~15=hP-22+12ρU-2,Π~16=6ρW-,Π~17=2ρZ-2,Π~25=-hP-22-6ρU-2,Π~18=-18ρU-2+6ρU-1,Π~26=2ρZ-2T,Π~23=-ρZ-1T-ρZ-2T-2ρW-,Π~27=6ρW-,Π~28=12ρU-2,Π~36=6ρW-+2ρZ-2T,Π~37=6ρW-+2ρZ-2,Π~58=12ρU-1+24ρU-2,Π~67=-4ρZ-2,Π~19=12hP-11AT,Π~39=12hYTB1T,Π~49=12hB2T,Π~1,10=12hP-11AT,Π~3,10=12hYTB1T,Π~4,10=12hB2T,Π~1,11=hP-11AT,Π~3,11=hYTB1T,Π~4,11=hB2T,Π~1,12=P-11CT,Π~3,12=YTDT,Π~99=12U-1-P-11,Π~10,10=12U-2-P-11,Π~11,11=W--2P-11,Π~12,12=-e-αTI,others(48)Π~ij=0,Σ11=-e-αTc2H1,Σ22=-H2,Σ33=-H3,Σ44=-H4,Σ55=-H5,Σ66=-H6,Σ77=-H7,Σ88=-H8,Σ99=-γ2d,Σ12=c1H2,Σ13=h2c1H3,Σ14=ρhc1H4,Σ15=ρhc1H5,Σ16=12ρh3c1H6,Σ17=16ρh3c1H7,Σ18=13ρh3c1H8,Σ19=P-11,others(49)Σij=0then a state feedbackH∞ controller in form of (7) exists, such that(1) the closed-loop system (8) with ut=0 is FTB;(2) under given nonzero initial condition, the closed system (8) and (9) guarantees that J=∫0TzTszs-γ2ωTsωs-γ21/TxT0Sx0ds<0 for all nonzero ωt and t∈0,T.The controller gain can be calculated byK=YP-11-1.Proof.
In preparation for designing, we setM=γ2I, β=1 for (37); then (37) and (38) can be rewritten as follows: (50)V˙-αV-γ2ωTtωt<ξTtΩ^ξt(51)Vt<eαtV0+γ2∫0teαt-sωTsωsds<eαTV0+γ2d.where(52)Ω^44=B2T12h22W+U1+U2B2-γ2I,Ω^ij=Ωij
Then, two steps are provided to design the desired controller.
Step  1. Here, we will give some conditions that can guarantee the H∞ performance over the finite-time interval under nonzero initial conditions firstly.
Consider the following inequality:(53)V˙-αV+eαtzTtzt-γ2eαtωTtωt<V˙-αV+eαTzTtzt-γ2ωTtωt<ξTtΩ^-ΨT-e-αTI-1Ψξt.
Noting thatW,U1, and U2 are coupled with A, B1K, and B2 in Ω^, to decouple these terms, the Ω^ can be rewritten as(54)Ω^=Ω~-Ψ~T-12U1-1Ψ~-Ψ-T-12U2-1Ψ--Ψ^T-W-1Ψ^where(55)Ω~11=ATP11+P11A-αP11+Q1+Q2-4ρW-3ρU1-9ρU2,Ω~33=-8ρW+ρZ1T+ρZ1-ρZ2T-ρZ2-1-μQ2,Ω~44=-γ2I,Ω~13=P11B1K-2ρW-ρZ1-ρZ2,Ω~14=P11B2,Ω~34=0,others(56)Ω~ij=ΩijΨ=C0DK00000Ψ~=h12U1TA0h12U1TB1Kh12U1TB20000.Ψ-=h12U2TA0h12U2TB1Kh12U2TB20000Ψ^=hWTA0hWTB1KhWTB20000.
By Schur complement,Ω^<0 and Ω^-ΨT-e-αTI-1Ψ are equivalent to(57)Π=Ω~Ψ~TΨ-TΨ^TΨT∗-12U1000∗∗-12U200∗∗∗-W0∗∗∗∗-e-αTI<0.
To ensure the proposed conditions satisfy theH∞ performance, we set the inequality like(58)P11-γ2S<0.
from which we have(59)V˙-αV+eαtzTtzt-γ2eαtωTtωt-γ2eαt1TxT0Sx0<V˙-αV+eαtzTtzt-γ2eαtωTtωt-γ2eαt1TxT0Sx0+eαt1TxT0P11x0<V˙-αV+eαtzTtzt-γ2eαtωTtωt+eαt1TxT0P11-γ2Sx0<0
Integrating (58) from 0 to T, we can obtain(60)∫0TzTszsds-∫0Tγ2ωTsωsds-γ2xT0Sx0<-∫0Te-αtV˙-αe-αtVds<0
so conditions (43), (44), (57), and (58) with the inequalities as follows can ensure that systems (17) and (18) satisfy the H∞ performance:(61)c1θ2+h2c1θ3+ρhc1θ4+ρhc1θ5+12ρh3c1θ6+16ρh3c1θ7+13ρh3c1θ8+γ2d<e-αTc2θ10<θ1I<P11<θ2I,0<P22<θ3I,0<Q1<θ4I,0<Q2<θ5I,0<W<θ6I,0<U1<θ7I,0<U2<θ8I.
Step  2. In this step, the approach to design the gain matrix K of the controller is provided in forms of LMIs, which can be calculated expediently.
To linearize the nonlinear terms in (57), we make it multiply by the following matrix from both left and right sides firstly:(62)diagP11-1P11-1P11-1IP11-1P11-1P11-1P11-1U1-1U2-1W-1I
Let us do the definitions as follows:(63)P-11=P11-1,Q-1=P11-1Q1P11-1,Q-2=P11-1Q2P11-1,W-=P11-1WP11-1,U-1=P11-1U1P11-1,U-2=P11-1U2P11-1,P-22=P11-1P22P11-1,Z-1=P11-1Z1P11-1,Z-2=P11-1Z2P11-1,Y=KP11-1.
so the inequalityΠ-<0 can guarantee Π<0 where(64)Π-99=-12P-11U-1-1P-11,Π-10,10=-12P-11U-2-1P-11,Π-11,11=-P-11W--1P-11,others(65)Π-ij=Π~ij.
Then, based on the inequalities-1/2P-11U-1-1P-11≤1/2U-1-P-11, -1/2P-11U-2-1P-11≤1/2U-2-P-11, -P-11W--1P-11≤W--2P-11, condition (57) can be converted into (41) in form of LMIs.
Accordingly, similar to the above-mentioned procedures, (61) can be transformed into (42) with the Schur complement and the definition of Hi=P11-1θiP11-1i=1,2,⋯,8.
Therefore, conditions (41) to (45) can obtain the controller in the form of (7) guaranteeing the desired performance. This completes the proof.Remark 16.
TheH∞ performance with nonzero initial condition is studied in this literature. In a practical view, it is hard to suffer the worst-case over a finite time for surface vessel with nonzero initial condition and it will reduce the conservatism caused by the assumption of zero initial condition. Therefore, it is reasonable to introduce such H∞ performance index to handle the problem of finite-time H∞ control for ship subject to exogenous signals.Remark 17.
It is challenging to achieve the result satisfying the control objective while it is very different from the standardH∞ control because a weighting diagonal matrix is introduced, especially to establish the form of LMIs. In the proof of Theorem 15, inequality (58) is introduced to ensure the H∞ performance with nonzero initial condition and make it convenient to construct the conditions in form of LMIs.Remark 18.
By introducing some new additional matrix variables, Cone Complementarity Linearization algorithm (CCL) [32] can be utilized to linearize the nonlinear terms as an alternative method. It will reduce the conservatism at the expense of increasing the computational burden and the number of decision variables.


## 3.1. FTB Analysis of DP System

Firstly, the result guaranteeing the FTB of DP system is established in this subsection.Theorem 13.
Given five positive scalarsα, β, c1,c2,T and positive define matrix R, the finite-time boundedness problem of system (4) is solvable if there exist positive scalars θll=1,2,⋯,8 and matrices P11>0, P22>0, W>0, Qi>0i=1,2, Uj>0j=1,2, M>0, Z1, Z2 with appropriate dimensions, satisfying the following conditions:(17)Ω=Ωij8×8<0(18)WZ1∗W>0(19)3WZ2∗3W>0(20)c1θ2+h2c1θ3+ρhc1θ4+ρhc1θ5+12ρh3c1θ6+16ρh3c1θ7+13ρh3c1θ8+βθ9d<e-αTc2θ1where(21)Ω11=ATP11+P11A-αP11+Q1+Q2+AT12h2U1+U2+2WA-4ρW-3ρU1-9ρU2,Ω22=-ρQ2-4ρW-6ρU2,Ω33=KTB1T12h22W+U1+U2B1K-8ρW+ρZ1T+ρZ1-ρZ2T-ρZ2-1-μQ2,Ω44=B2T12h22W+U1+U2B2-βM,Ω66=-12ρW,Ω77=-12ρW,Ω55=αh2P22-18ρU2-6ρU1,Ω88=-36ρU1-36ρU2,Ω12=ρZ1-ρZ2+6ρU2,Ω15=hP22+12ρU2,Ω16=6ρW,Ω17=2ρZ2,Ω13=P11B1K+AT12h22W+U1+U2B1K-2ρW-ρZ1-ρZ2,Ω14=P11B2+AT12h22W+U1+U2B2,Ω18=-18ρU2+6ρU1,Ω23=-ρZ1T-ρZ2T-2ρW,Ω25=-hP22-6ρU2,Ω26=2ρZ2T,Ω27=6ρW,Ω28=12ρU2,Ω34=KTB1T12h22W+U1+U2B2,Ω36=6ρW+2ρZ2T,Ω37=6ρW+2ρZ2,Ω58=12ρU1+24ρU2,Ω67=-4ρZ2,Ω24=Ω35=Ω38=Ω45=Ω46=Ω47=Ω48=Ω56=Ω57=Ω68=Ω78=0,θ1=λminP~11θ2=λmaxP~11,θ3=λmaxP~22,θ4=λmaxQ~1,θ5=λmaxQ~2,θ6=λmaxW~,θ7=λmaxU~1,θ8=λmaxU~2,θ9=λmaxM,ρ=eαh,P~11=R-1/2P11R-1/2,P~22=R-1/2P22R-1/2,Q~i=R-1/2QiR-1/2i=1,2,3,W~=R-1/2WR-1/2,U~j=R-1/2UjR-1/2j=1,2,0<θ1I<P11<θ2I,0<P22<θ3I,0<Q1<θ4I,0<Q2<θ5I,0<W<θ6I,0<U1<θ7I,0<U2<θ8I,0<M<θ9I.Proof.
Consider the candidate augment LKLF as follows:(22)Vt=V1t+V2t+V3t+V4t(23)V1t=εtTPεt(24)V2t=∫t-hteαt-sxsTQ1xsds+∫t-htteαt-sxsTQ2xsds(25)V3t=h∫-h0∫t+θteαt-sx˙sTWx˙sdsdθ(26)V4t=∫-h0∫θ0∫t+βteαt-sx˙sTU1x˙sdsdβdθ+∫-h0∫-hθ∫t+βteαt-sx˙sTU2x˙sdsdβdθwhere εt=xt∫t-htxsdsP=P110∗P22.
To deal with the formulas conveniently, let us provide such definitions:(27)ξt=xtxt-hxt-htωt1h∫t-htxsds1ht∫t-httxsds1h-ht∫t-ht-htxsds1h2∫-h0∫t+θtxsdsdθlkT=0⋯0︸k-110⋯0︸8-k.
The time-derivative ofVt along system (4) can be bounded as (28)V˙1t=αV1t+ε˙tTPεt+εtTPε˙t-αV1t(29)V˙2t=αV2t+xtTQ1xt-eαhxt-hTQ1xt-h+xtTQ2xt-1-h˙teαhtxt-htTQ2xt-ht≤αV2t+xtTQ1xt-eαhxt-hTQ1xt-h+xtTQ2xt-1-μxt-htTQ2xt-ht(30)V˙3t=αV3t+h2x˙tTW2x˙t-eαhh∫t-htx˙sTW2x˙sds(31)V˙4t=αV4t+12h2x˙tTU1x˙t-eαh∫-h0∫t+βtx˙sTU1x˙sdsdβ+12h2x˙tTU2x˙t-eαh∫-h0∫t-ht+βx˙sTU2x˙sdsdβ.
Invoking Lemma9, we can obtain(32)V˙3t=αV3t+h2x˙tTWx˙t-eαhh∫t-httx˙sTWx˙sds-eαhh∫t-ht-htx˙sTWx˙sds≤αV3t+h2x˙tTWx˙t-eαhhhtϖ1TΛ1ϖ1-eαhhh-htϖ2TΛ2ϖ2where(33)ϖ1T=ξTtl1T-l3TTl1T+l3T-2l6TTTϖ2T=ξTtl3T-l2TTl3T+l2T-2l7TTΛ1=Λ2=W0∗3W.
In order to obtain a tighter bound of integral term, Lemma11 is applied to (32) as follows:(34)V˙3t≤αV3t+h2x˙tTWx˙t-eαhϖ3TΛ3ϖ3where ϖ3T=ϖ1Tϖ2T, Λ3=WZ100∗W00∗∗3WZ2∗∗∗3W.
By applying Lemma10 to (31), we can obtain the inequality(35)V˙4t≤αV4t+12h2x˙tTU1x˙t+12h2x˙tTU2x˙t-eαhϖ4TΛ4ϖ4where(36)ϖ4T=ξTtl1T-l2TT12l1T-l8TTl2T-l5TT12l2T-l5T+l8TTTΛ4=6U1-12U100∗36U100∗∗6U2-12U2∗∗∗36U2.
Combining (28), (29), (34), and (35) with the definition of ρ=eαh, we can obtain(37)V˙-αV-βωTtMωt<ξTtΩξt.
Assuming thatΩ<0 and integrating the left part of inequality (37),(38)Vt<eαtV0+β∫0teαt-sωTsMωsds<eαTV0+βλmaxMd.
Invoking the Jensen inequality shown in Lemma12, one has(39)V0≤x0TP11x0+h∫-h0xsTP22xsds+ρ∫-h0xsTQ1xsds+ρ∫-ht0xsTQ2xsds+hρ∫-h0∫θ0x˙sTWx˙sdsdθ+ρ∫-h0∫θ0∫β0x˙sTU1x˙sdsdβdθ+ρ∫-h0∫-hθ∫β0x˙sTU2x˙sdsdβdθ≤λmaxP~11c1+hλmaxP~22hc1+ρλmaxQ~1hc1+ρλmaxQ~2hc1+ρλmaxW~12h3c1+ρλmaxU~116h3c1+ρλmaxU~213h3c1
Based on inequalities (38) and (39), we have(40)Vt>xTtP11xt=xTtR1/2P~11R1/2xt>λminP~11xTtRxt.
Therefore, conditions (17) to (20) can guarantee the FTB of system (4). This completes the proof.Remark 14.
Among the existing approaches, there are two threads: one is to construct a novel LKLF that involves more information of delay; the other is to find a tighter estimation of upper bound for cross terms coming from the derivative of the LKLF. In this paper, these two techniques are applied to obtain the result. In addition, the less conservatism in practical engineering will be shown in the simulations which are always ignored in most literature sources.


## 3.2. Controller Design

In this subsection, we focus on the problem of finite-timeH∞ state feedback designing based on Theorem 13, that is, designing a state feedback controller in the form of (7) such that the resulting DP system satisfies the control objective proposed in Section 1.Theorem 15.
For given positiveα, c1, c2, T, γ and matrices R>0, S≥0, if there exist positive scalars θll=1,2,⋯,8 and matrices P-11>0, P-22>0, W->0, Q-i>0i=1,2, U-j>0j=1,2, Y,Z-1,Z-2 with appropriate dimensions, satisfying the following conditions:(41)Π~=Π~ij12×12<0(42)Σ=Σij9×9<0(43)W-Z-1∗W->0(44)3W-Z-2∗3W->0(45)I-γ2SP-11<0(46)0<H1<P-11<H2,0<P-22<H3,0<Q-1<H4,0<Q-2<H5,0<W-<H6,0<U-1<H7,0<U-2<H8,where(47)Π~11=P-11AT+AP-11-αP-11+Q-1+Q-2-4ρW--3ρU-1-9ρU-2,Π~44=-γ2I,Π~22=-ρQ-2-4ρW--6ρU-2,Π~33=-8ρW-+ρZ-1T+ρZ-1-ρZ-2T-ρZ-2-1-μQ-2,Π~13=B1Y-2ρW--ρZ-1-ρZ-2,Π~14=B2,Π~66=-12ρW-,Π~77=-12ρW-,Π~55=αh2P-22-18ρU-2-6ρU-1,Π~88=-36ρU-1-36ρU-2,Π~12=ρZ-1-ρZ-2+6ρU-2,Π~15=hP-22+12ρU-2,Π~16=6ρW-,Π~17=2ρZ-2,Π~25=-hP-22-6ρU-2,Π~18=-18ρU-2+6ρU-1,Π~26=2ρZ-2T,Π~23=-ρZ-1T-ρZ-2T-2ρW-,Π~27=6ρW-,Π~28=12ρU-2,Π~36=6ρW-+2ρZ-2T,Π~37=6ρW-+2ρZ-2,Π~58=12ρU-1+24ρU-2,Π~67=-4ρZ-2,Π~19=12hP-11AT,Π~39=12hYTB1T,Π~49=12hB2T,Π~1,10=12hP-11AT,Π~3,10=12hYTB1T,Π~4,10=12hB2T,Π~1,11=hP-11AT,Π~3,11=hYTB1T,Π~4,11=hB2T,Π~1,12=P-11CT,Π~3,12=YTDT,Π~99=12U-1-P-11,Π~10,10=12U-2-P-11,Π~11,11=W--2P-11,Π~12,12=-e-αTI,others(48)Π~ij=0,Σ11=-e-αTc2H1,Σ22=-H2,Σ33=-H3,Σ44=-H4,Σ55=-H5,Σ66=-H6,Σ77=-H7,Σ88=-H8,Σ99=-γ2d,Σ12=c1H2,Σ13=h2c1H3,Σ14=ρhc1H4,Σ15=ρhc1H5,Σ16=12ρh3c1H6,Σ17=16ρh3c1H7,Σ18=13ρh3c1H8,Σ19=P-11,others(49)Σij=0then a state feedbackH∞ controller in form of (7) exists, such that(1) the closed-loop system (8) with ut=0 is FTB;(2) under given nonzero initial condition, the closed system (8) and (9) guarantees that J=∫0TzTszs-γ2ωTsωs-γ21/TxT0Sx0ds<0 for all nonzero ωt and t∈0,T.The controller gain can be calculated byK=YP-11-1.Proof.
In preparation for designing, we setM=γ2I, β=1 for (37); then (37) and (38) can be rewritten as follows: (50)V˙-αV-γ2ωTtωt<ξTtΩ^ξt(51)Vt<eαtV0+γ2∫0teαt-sωTsωsds<eαTV0+γ2d.where(52)Ω^44=B2T12h22W+U1+U2B2-γ2I,Ω^ij=Ωij
Then, two steps are provided to design the desired controller.
Step  1. Here, we will give some conditions that can guarantee the H∞ performance over the finite-time interval under nonzero initial conditions firstly.
Consider the following inequality:(53)V˙-αV+eαtzTtzt-γ2eαtωTtωt<V˙-αV+eαTzTtzt-γ2ωTtωt<ξTtΩ^-ΨT-e-αTI-1Ψξt.
Noting thatW,U1, and U2 are coupled with A, B1K, and B2 in Ω^, to decouple these terms, the Ω^ can be rewritten as(54)Ω^=Ω~-Ψ~T-12U1-1Ψ~-Ψ-T-12U2-1Ψ--Ψ^T-W-1Ψ^where(55)Ω~11=ATP11+P11A-αP11+Q1+Q2-4ρW-3ρU1-9ρU2,Ω~33=-8ρW+ρZ1T+ρZ1-ρZ2T-ρZ2-1-μQ2,Ω~44=-γ2I,Ω~13=P11B1K-2ρW-ρZ1-ρZ2,Ω~14=P11B2,Ω~34=0,others(56)Ω~ij=ΩijΨ=C0DK00000Ψ~=h12U1TA0h12U1TB1Kh12U1TB20000.Ψ-=h12U2TA0h12U2TB1Kh12U2TB20000Ψ^=hWTA0hWTB1KhWTB20000.
By Schur complement,Ω^<0 and Ω^-ΨT-e-αTI-1Ψ are equivalent to(57)Π=Ω~Ψ~TΨ-TΨ^TΨT∗-12U1000∗∗-12U200∗∗∗-W0∗∗∗∗-e-αTI<0.
To ensure the proposed conditions satisfy theH∞ performance, we set the inequality like(58)P11-γ2S<0.
from which we have(59)V˙-αV+eαtzTtzt-γ2eαtωTtωt-γ2eαt1TxT0Sx0<V˙-αV+eαtzTtzt-γ2eαtωTtωt-γ2eαt1TxT0Sx0+eαt1TxT0P11x0<V˙-αV+eαtzTtzt-γ2eαtωTtωt+eαt1TxT0P11-γ2Sx0<0
Integrating (58) from 0 to T, we can obtain(60)∫0TzTszsds-∫0Tγ2ωTsωsds-γ2xT0Sx0<-∫0Te-αtV˙-αe-αtVds<0
so conditions (43), (44), (57), and (58) with the inequalities as follows can ensure that systems (17) and (18) satisfy the H∞ performance:(61)c1θ2+h2c1θ3+ρhc1θ4+ρhc1θ5+12ρh3c1θ6+16ρh3c1θ7+13ρh3c1θ8+γ2d<e-αTc2θ10<θ1I<P11<θ2I,0<P22<θ3I,0<Q1<θ4I,0<Q2<θ5I,0<W<θ6I,0<U1<θ7I,0<U2<θ8I.
Step  2. In this step, the approach to design the gain matrix K of the controller is provided in forms of LMIs, which can be calculated expediently.
To linearize the nonlinear terms in (57), we make it multiply by the following matrix from both left and right sides firstly:(62)diagP11-1P11-1P11-1IP11-1P11-1P11-1P11-1U1-1U2-1W-1I
Let us do the definitions as follows:(63)P-11=P11-1,Q-1=P11-1Q1P11-1,Q-2=P11-1Q2P11-1,W-=P11-1WP11-1,U-1=P11-1U1P11-1,U-2=P11-1U2P11-1,P-22=P11-1P22P11-1,Z-1=P11-1Z1P11-1,Z-2=P11-1Z2P11-1,Y=KP11-1.
so the inequalityΠ-<0 can guarantee Π<0 where(64)Π-99=-12P-11U-1-1P-11,Π-10,10=-12P-11U-2-1P-11,Π-11,11=-P-11W--1P-11,others(65)Π-ij=Π~ij.
Then, based on the inequalities-1/2P-11U-1-1P-11≤1/2U-1-P-11, -1/2P-11U-2-1P-11≤1/2U-2-P-11, -P-11W--1P-11≤W--2P-11, condition (57) can be converted into (41) in form of LMIs.
Accordingly, similar to the above-mentioned procedures, (61) can be transformed into (42) with the Schur complement and the definition of Hi=P11-1θiP11-1i=1,2,⋯,8.
Therefore, conditions (41) to (45) can obtain the controller in the form of (7) guaranteeing the desired performance. This completes the proof.Remark 16.
TheH∞ performance with nonzero initial condition is studied in this literature. In a practical view, it is hard to suffer the worst-case over a finite time for surface vessel with nonzero initial condition and it will reduce the conservatism caused by the assumption of zero initial condition. Therefore, it is reasonable to introduce such H∞ performance index to handle the problem of finite-time H∞ control for ship subject to exogenous signals.Remark 17.
It is challenging to achieve the result satisfying the control objective while it is very different from the standardH∞ control because a weighting diagonal matrix is introduced, especially to establish the form of LMIs. In the proof of Theorem 15, inequality (58) is introduced to ensure the H∞ performance with nonzero initial condition and make it convenient to construct the conditions in form of LMIs.Remark 18.
By introducing some new additional matrix variables, Cone Complementarity Linearization algorithm (CCL) [32] can be utilized to linearize the nonlinear terms as an alternative method. It will reduce the conservatism at the expense of increasing the computational burden and the number of decision variables.


## 4. Simulations

### 4.1. Simulation Settings

To demonstrate the effectiveness and superiority of the robust finite-timeH∞ control scheme, simulation studies are conducted on the parameters of the ship CyberShip II [33], which is a 1:70 scale-replica of a supply ship whose main parameters are shown in Table 1. In addition, we choose the time-varying function like ht=3sint/6-π/6 to describe the time delay occurred in the input signal.Table 1
The main parameters of the CyberShip II.
m 23.8000 Xu˙ -2.0 Xu -0.7225 Iz 1.7600 Yv˙ -10.0 Yv -0.8612 xg 0.0460 Yr˙ -0.0 Yr 0.1079 Nr˙ -1.0 Nr 0.5Unknown external disturbancesωt with significantly large magnitude and high frequency, which can be roughly considered as complex environment including ocean winds, waves, and currents, are governed by [34](66)ωt=9sin0.1πt-π56sin0.3πt+π63sin0.2πt+π3with initial conditions η0=110.1 and υ0=0.80.60.1.


### 4.2. Numerical Simulations

We chooseγ=1.3,T=10,S=0.3∗I,c1=3.02,c2=10,α=0.001. By using Theorem 15, the control gain K is calculated by LMIs (41) to (45):(67)K=-3.274300-31.3907000-4.2784-0.15720-41.2136-1.29820-0.1389-0.34970-1.3362-3.3091.To demonstrate the superiority and validity, three scenarios as comparative cases are provided here. It should be pointed out that the results within 100s are also provided to illustrate the steady-state performance.Case 1 (with differentS).
For comparison purposes, we setS with different value to demonstrate the effect of S on state response. Without loss of generality, we set S=0.5∗I and S=0.1∗I, respectively.Case 2 (H∞ with zero initial condition).
This scenario will show that the control law proposed in this paper can achieve a better transient performance and disturbance rejection capability over traditionalH∞ control approach for dynamic positioning system conducted in [11].Case 3 (a control design based on existing methods).
Based on the approach in [17] applied for discrete-time system, a control law for dynamic positioning ship with input delay is proposed to illustrate the less conservatism of our designing approach in practical engineering subsequently.At first, the effectiveness of the control law we designed is confirmed from Figures1–6. Figure 1 shows the state response of xTtRxt. Obviously, from that curve we can see that the value of xTtRxt is far below the value of c2=10 in the presence of disturbance as in Figure 2, which means the finite-time full-state feedback controller designed can guarantee the DP system (8) ~ (9) FTB with 3.0210d103I and have less conservatism, where we set d=∫0TωtTωtdt. Meanwhile, the control law can stabilize the dynamic positioning ship with minimum steady-state error in 100s and the control input will be small enough as shown in Figure 6. From Figures 3–5, we can find that all states in DP system are within a small range. As shown in Figures 2–4, the angle and the angular velocity in yaw have changed within 0.1°, which means that the heading of the vessel stays in a fixed direction. Furthermore, the velocities in surge and sway are low enough, which illustrates that assumption 2 is reasonable and it meets the requirement of stabilization control for DP system.Figure 1
State responsexTtRxt of DP system.Figure 2
Disturbance in surge, sway, and yaw.Figure 3
State responses of position and orientation for DP System.Figure 4
State responses of velocities for DP system.Figure 5
Trajectory of the ship’s horizontal motion.Figure 6
Control inputs.To demonstrate the effect ofS, state responses of systems with different S are exhibited in Figures 7–9. As the value of S decreases, the restriction for P11 is more exclusive and the robustness is stronger during preset time interval as in Figures 7 and 8 while the required control input will increase dramatically as in Figure 9. When the time oversteps the preset time interval, all the states can be guaranteed within the given upper bound as before.Figure 7
State responsexTtRxt with different S.Figure 8
State responses of position and orientation with differentS.Figure 9
Control input with differentS.As shown in Figures10–12, the overconservatism of traditional H∞ control approach applied in DP ship is solved by the H∞ control strategy with nonzero initial condition proposed in this article. As is well known, the classical H∞ control law is designed under the so-called worst-case norm while the performance of antidisturbance and transient is sacrificed to some degree. From Figures 10 and 11 we can see that the state response can be controlled in a smaller range and stabilized in a shorter time with a lower overshoot shown in Figure 12. Hence, a conclusion can be drawn that the control law we present can achieve a better disturbance rejection capability and transient performance while the matter of overconservatism can be resolved at the same time.Figure 10
State responsexTtRxt of Theorem 15 and Case 2.Figure 11
Position and orientation of Theorem15 and Case 2.Figure 12
Trajectory of the ship’s horizontal motion of Theorem15 and Case 2.Simulation results of Theorem15 and Case 3 are shown in Figures 13 and 14 to show the better performance of the method we proposed. We can find that the controller based on [17] and H∞ control approach present in this literature can make all states of system within a small enough region. However, compared with the controller we constructed, the state response has higher overshoot which will affect the control precision and transient performance in practical engineering. Based on the above simulation results, the developed controller can achieve a higher accuracy and lower overshoot, which means that it is less conservative in comparison with existing result.Figure 13
State responsexTtRxt of Theorem 15 and Case 3.Figure 14
Position and orientation of Theorem15 and Case 3.


## 4.1. Simulation Settings

To demonstrate the effectiveness and superiority of the robust finite-timeH∞ control scheme, simulation studies are conducted on the parameters of the ship CyberShip II [33], which is a 1:70 scale-replica of a supply ship whose main parameters are shown in Table 1. In addition, we choose the time-varying function like ht=3sint/6-π/6 to describe the time delay occurred in the input signal.Table 1
The main parameters of the CyberShip II.
m 23.8000 Xu˙ -2.0 Xu -0.7225 Iz 1.7600 Yv˙ -10.0 Yv -0.8612 xg 0.0460 Yr˙ -0.0 Yr 0.1079 Nr˙ -1.0 Nr 0.5Unknown external disturbancesωt with significantly large magnitude and high frequency, which can be roughly considered as complex environment including ocean winds, waves, and currents, are governed by [34](66)ωt=9sin0.1πt-π56sin0.3πt+π63sin0.2πt+π3with initial conditions η0=110.1 and υ0=0.80.60.1.


## 4.2. Numerical Simulations

We chooseγ=1.3,T=10,S=0.3∗I,c1=3.02,c2=10,α=0.001. By using Theorem 15, the control gain K is calculated by LMIs (41) to (45):(67)K=-3.274300-31.3907000-4.2784-0.15720-41.2136-1.29820-0.1389-0.34970-1.3362-3.3091.To demonstrate the superiority and validity, three scenarios as comparative cases are provided here. It should be pointed out that the results within 100s are also provided to illustrate the steady-state performance.Case 1 (with differentS).
For comparison purposes, we setS with different value to demonstrate the effect of S on state response. Without loss of generality, we set S=0.5∗I and S=0.1∗I, respectively.Case 2 (H∞ with zero initial condition).
This scenario will show that the control law proposed in this paper can achieve a better transient performance and disturbance rejection capability over traditionalH∞ control approach for dynamic positioning system conducted in [11].Case 3 (a control design based on existing methods).
Based on the approach in [17] applied for discrete-time system, a control law for dynamic positioning ship with input delay is proposed to illustrate the less conservatism of our designing approach in practical engineering subsequently.At first, the effectiveness of the control law we designed is confirmed from Figures1–6. Figure 1 shows the state response of xTtRxt. Obviously, from that curve we can see that the value of xTtRxt is far below the value of c2=10 in the presence of disturbance as in Figure 2, which means the finite-time full-state feedback controller designed can guarantee the DP system (8) ~ (9) FTB with 3.0210d103I and have less conservatism, where we set d=∫0TωtTωtdt. Meanwhile, the control law can stabilize the dynamic positioning ship with minimum steady-state error in 100s and the control input will be small enough as shown in Figure 6. From Figures 3–5, we can find that all states in DP system are within a small range. As shown in Figures 2–4, the angle and the angular velocity in yaw have changed within 0.1°, which means that the heading of the vessel stays in a fixed direction. Furthermore, the velocities in surge and sway are low enough, which illustrates that assumption 2 is reasonable and it meets the requirement of stabilization control for DP system.Figure 1
State responsexTtRxt of DP system.Figure 2
Disturbance in surge, sway, and yaw.Figure 3
State responses of position and orientation for DP System.Figure 4
State responses of velocities for DP system.Figure 5
Trajectory of the ship’s horizontal motion.Figure 6
Control inputs.To demonstrate the effect ofS, state responses of systems with different S are exhibited in Figures 7–9. As the value of S decreases, the restriction for P11 is more exclusive and the robustness is stronger during preset time interval as in Figures 7 and 8 while the required control input will increase dramatically as in Figure 9. When the time oversteps the preset time interval, all the states can be guaranteed within the given upper bound as before.Figure 7
State responsexTtRxt with different S.Figure 8
State responses of position and orientation with differentS.Figure 9
Control input with differentS.As shown in Figures10–12, the overconservatism of traditional H∞ control approach applied in DP ship is solved by the H∞ control strategy with nonzero initial condition proposed in this article. As is well known, the classical H∞ control law is designed under the so-called worst-case norm while the performance of antidisturbance and transient is sacrificed to some degree. From Figures 10 and 11 we can see that the state response can be controlled in a smaller range and stabilized in a shorter time with a lower overshoot shown in Figure 12. Hence, a conclusion can be drawn that the control law we present can achieve a better disturbance rejection capability and transient performance while the matter of overconservatism can be resolved at the same time.Figure 10
State responsexTtRxt of Theorem 15 and Case 2.Figure 11
Position and orientation of Theorem15 and Case 2.Figure 12
Trajectory of the ship’s horizontal motion of Theorem15 and Case 2.Simulation results of Theorem15 and Case 3 are shown in Figures 13 and 14 to show the better performance of the method we proposed. We can find that the controller based on [17] and H∞ control approach present in this literature can make all states of system within a small enough region. However, compared with the controller we constructed, the state response has higher overshoot which will affect the control precision and transient performance in practical engineering. Based on the above simulation results, the developed controller can achieve a higher accuracy and lower overshoot, which means that it is less conservative in comparison with existing result.Figure 13
State responsexTtRxt of Theorem 15 and Case 3.Figure 14
Position and orientation of Theorem15 and Case 3.


## 5. Conclusion

In this paper, the robust finite-timeH∞ control with transients for DP system with input delay, maintaining all states of ocean surface vessel into a given threshold over a fixed time interval in presence of time-varying disturbance, is proposed. Based on a novel augmented LKLF with triple integral terms and a method combining the Wirtinger inequality and reciprocally convex approach, a less conservative result is derived. In particular, a H∞ performance index with nonzero initial condition, attenuating the overconservatism caused by the assumption of zero initial condition and enhancing the transient performance of ship subject to external disturbance, is adopted. The obtained result is formulated in terms of LMIs which can be easily solved by the standard numerical software. Finally, a numerical simulation for a ship is proposed to verify the effectiveness and less conservatism of the controller we designed. In the future, the output feedback control can be developed for the ocean surface vessel to avoid the use of the vessel-frame surge, sway, and yaw velocities.



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*Source: 2838749-2018-06-26.xml*