# Improvement of the Angle of Arrival Measurement Accuracy for Indoor UWB Localization

Authors: N. Awarkeh; J.-C. Cousin; M. Muller; N. Samama
Journal: Journal of Sensors
 (2020)

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## Abstract

This paper shows that the accuracy of azimuth angle measurement for an interferometric localization system used to locate tags in its Line-of-Sight (LoS) can be improved by exploiting Impulse Radio-Ultra WideBand (IR-UWB) signals and without increasing the frequency bandwidth. This solution uses a Phase Correlation (PC) method, initially applied for Continuous Wave (CW) signals, adapted for Ultra WideBand (UWB) pulse signals. The obtained results are compared to those computed by a classical Energy Detection (ED) method where it becomes impossible to estimate azimuth angles for tag positions close to the orthogonal centered axis of the localization system baseline.


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## Body

## 1. Introduction

In recent years, indoor localization has gained interest due to the vast range of services it can offer in many areas and applications. Many positioning technologies can be used within an indoor localization system depending on the intended accuracy, precision, cost, etc. The Global Navigation Satellite System (GNSS) is not accurate enough to provide specific services. Complementary systems have been developed to insure reliability and accuracy, even in hard conditions (multipaths, shadowing, …). A solution is to use the time propagation of IR-UWB signal by exploiting wide frequency bandwidths and naturally increasing the accuracy.Different approaches for UWB’s estimated ToA are addressed in the literature. In [1], the performance of two different position estimation methods based on ToA estimation of the UWB signal for a set of receivers/sensors is investigated. The first one is based on the direct calculation method which gives the exact range (distance) between a tag and a sensor. The second one examines classical nonlinear optimization techniques, and more precisely the Davidon-Fletcher-Powell quasi-Newton algorithm. The optimal position is estimated by minimizing the summation of the quadratic errors for all the sensors. In [2], the problem of distance estimation in a dense multipath environment is studied by applying a technique that relies on the analysis of the power delay profile of the received UWB signal and the theory of segmentation of nonstationary processes. In [3], an algorithm combining match filtering and peak search techniques is presented to accurately determine the ToA of the received signal.Most of the algorithms mentioned above are based on the ToA estimate of the strongest path. However, since the strongest path is not necessarily the first arrival path in dense multipath channels, their ToA accuracy is limited. Similarly, in some algorithms, prior knowledge of the received pulse shape also adds limitations to the ToA estimate. Therefore, with the change in shape of the different multipath components, it is more difficult to adapt exactly to the received pulse shape.Due to these limitations, several solutions were proposed. In the first one, the detection is simplified by sending two pulses simultaneously so that the deformation affecting them will be the same. For instance, a two-step ToA estimation based on the time delayed sampling and correlation method for Transmitted-Reference UWB (TR-UWB) signals is presented in [4]. Another solution is based on energy detection, where energy is collected after certain analog front-end processing. In [5], the performance of three approaches based on ToA estimation techniques is analyzed for IR-UWB systems using sub-Nyquist sampling rates. These schemes, namely, Stored-Reference (SR), Transmitted-Reference (TR), and Energy Detection (ED), are used to collect the energy of the received signal. In [6], a two-step strategy based on SR and ED is applied to estimate the ToA, using a signal that corresponds to the IEEE 802.15.4a standard. The first step consists in finding the block with the highest energy. The second step consists in finding the chip where the first signal path is located, by correlating the received signal with a shifted version of the template signal. In [7], various ToA estimation algorithms for UWB systems are analyzed. These algorithms use a low sampling rate and three variants of the ED method, namely, Maximum Energy Selection (MES), Threshold Comparison (TC), and Maximum Energy Selection with Search-Back (MES-SB).These algorithms do not require precise synchronization or pulse shapes but rather need a strong signal at the detector input. This requirement is crucial since the ToA estimation is seen as a problem of detecting the leading edge of the signal, which can be erroneous when the noise power is higher than the signal power.Therefore, even if it is theoretically possible to obtain very accurate ranging, the practical limitations of the above algorithms prevent the localization system from achieving the desired high resolution. At the same time, a trade-off between the required accuracy, resolution, and complexity must be taken into account when developing a ToA estimation algorithm. To this end, we propose in this paper an alternative solution of low complexity based on Phase Correlation method adapted to IR-UWB signals, improving the accuracy and resolution of the azimuth angle measurement for an interferometric localization system. The main advantage of an interferometric method is that the position of a person/object in a room without obstacles can be obtained using only one fixed anchor instead of a well-known constellation.


## 2. Localization System Design

The 2D localization system, shown in Figure1, consists of two main parts: the Localization Base Station (LBS) and an IR-UWB Tx-Chain to be localized.Figure 1
Architecture of the localization system.


### 2.1. Tx-Chain Architecture

The IR-UWB Tx-Chain architecture is depicted in Figure2.Figure 2
Architecture of the IR-UWB Tx-Chain.A square signal generator drives an impulse generator. In order to optimize the useful energy of the pulse in the bandwidth ofA0, the UWB pulse has been filtered by a band-pass filter (3-7 GHz) and next amplified by a LNA.The obtained pulses at the output of the impulse generator, with a durationT equal to 2 ns, and at the input of the antenna A0, with a duration T′>T, are shown in Figures 3(a) and 3(b), respectively. T′ is longer than T, and this is due to the distortions mainly caused by the group delay of the band-pass filter and the amplifier.Figure 3
Shapes of the generated IR-UWB signal.
(a)
The pulse at the impulse generator output(b)
The pulse at the antennaA0 input


### 2.2. Rx-Chain Architecture

The LBS architecture comprises two RF receiver chains (Rx-Chain), each connected to its own antenna,A1 and A2, respectively. These two antennas are placed on the same axis forming the baseline (dbaseline). The two Rx-Chains are identical and shown in Figure 4.Figure 4
Architecture of the Rx-Chains.The signal coming from the IR-UWB Tx-Chain is received by the two Rx-Chain antennas (A1 and A2) of the LBS. The received signals are amplified by a wideband LNA and then filtered by a band-pass filter (3-7 GHz). The acquisition system is an Agilent (Keysight) Infinium MSO 9254A acquiring simultaneously the two signals at the output of the band-pass filters.


## 2.1. Tx-Chain Architecture

The IR-UWB Tx-Chain architecture is depicted in Figure2.Figure 2
Architecture of the IR-UWB Tx-Chain.A square signal generator drives an impulse generator. In order to optimize the useful energy of the pulse in the bandwidth ofA0, the UWB pulse has been filtered by a band-pass filter (3-7 GHz) and next amplified by a LNA.The obtained pulses at the output of the impulse generator, with a durationT equal to 2 ns, and at the input of the antenna A0, with a duration T′>T, are shown in Figures 3(a) and 3(b), respectively. T′ is longer than T, and this is due to the distortions mainly caused by the group delay of the band-pass filter and the amplifier.Figure 3
Shapes of the generated IR-UWB signal.
(a)
The pulse at the impulse generator output(b)
The pulse at the antennaA0 input


## 2.2. Rx-Chain Architecture

The LBS architecture comprises two RF receiver chains (Rx-Chain), each connected to its own antenna,A1 and A2, respectively. These two antennas are placed on the same axis forming the baseline (dbaseline). The two Rx-Chains are identical and shown in Figure 4.Figure 4
Architecture of the Rx-Chains.The signal coming from the IR-UWB Tx-Chain is received by the two Rx-Chain antennas (A1 and A2) of the LBS. The received signals are amplified by a wideband LNA and then filtered by a band-pass filter (3-7 GHz). The acquisition system is an Agilent (Keysight) Infinium MSO 9254A acquiring simultaneously the two signals at the output of the band-pass filters.


## 3. Azimuth Angleα Computation and Limitations

The separation of the two receiving antennasA1 and A2 by dbaseline creates a path difference (Path-dif) between two independent incoming signals (Signal 1 and Signal 2) which, in turn, gives the time difference Δt=T2−T1.
(1)Path‐dif=c.Δt.On the other hand, for Signal 1 and Signal 2 being two plane waves, the Path-dif between these two parallel signals at an angleα with the baseline is given by the base length (AC) of the right-angle triangle ABC. This assumption is only valid for a plane wave if the parallelism condition between the distances d1 and d2 is satisfied. Therefore, to fulfill this condition, we assume that d1 and d2 are large enough compared to dbaseline [8].
(2)Path‐dif=dbaseline.cosα.The azimuth angleα measurement is computed as below [9]:
(3)α=cos−1cT2−T1dbaseline,where T1 and T2 are the time of flight of the signal over d1 and d2 and c is the speed of light.The pulse signal used for UWB radar applications generally covers the 3-5 GHz bandwidth, calledΔf, which is the lower part of the UWB spectrum [10]. In general, the smallest Path-dif that the system can detect is equal to c/2Δf. In our case, for a frequency bandwidth of 2 GHz, the Path-dif is 15 cm and the time difference ∣T2−T1∣ is 0.5 ns. So, using a dbaseline=29cm, it becomes impossible to estimate the azimuth angle α in a range of [60°-120°] due to a Path-dif less than 15 cm.To improve the accuracy of the azimuth angle measurement without increasing the frequency bandwidth, many solutions are proposed, such as [11] which exploits the phase difference of a CW signal. With a dbaseline=29cm and a CW signal at 2.45 GHz, the azimuth angle uncertainty range is equal to +/-2°. The major drawback of these solutions is that the accuracy is affected by the multipath channel environment even in LoS situation.An alternative solution to improve this accuracy is to exploit the distortion of the generated UWB pulse signal by the LBS (Tx-Chain and/or Rx-Chains) and the antennas instead of relying on CW signal. This method will be detailed in the next section.


## 4. Accuracy Improvement for the Path-dif/Azimuth Angle Estimation

The complete setup, shown in Figure5, is composed by one RF transmitter chain linked to a circular polarized antenna A0 and two RF receiver chains connected to two UWB horn antennas A1 and A2. The distance between A1 and A2 is denoted by dbaseline.Figure 5
Test bench to measure the azimuth angleα.To improve the resolution of the path difference measurement between Signal 1 and Signal 2, the antennaA0 can take 31 different positions pi with i∈−15,⋯,15, as shown in Figure 6. At the initial position p0, the antenna A0 is placed on an orthogonal axis at 1.5 m from the center of dbaseline, here equal to 29 cm. The choice of dbaseline equal to 29 cm is determined by the trade-off between the available equipment, the size of the receiving antennas A1 and A2, and the minimum value to insure a theoretical azimuth angle step measurement better than 1°. To validate the angular resolution improvement obtained with the PC method, A0 can occupy several positions on a straight line parallel to the baseline, by shifting it 2 cm on each side of its initial position p0 in the range (-30 cm; 30 cm). The distance between A0 and A1 (resp., A2) is denoted d1 (resp., d2). The path difference between the two received signals, Signal 1 and Signal 2, denoted Path‐diff=d1−d2 is expressed in terms of the difference between their arrival times T1 and T2 at antennas A1 and A2, respectively. For this configuration, the maximum actual path difference corresponding to the positions p−15 and p15 is equal to 5.7 cm.Figure 6
Possible positions ofA0.In Figure7, the recorded signals for the initial position p0 are presented.Figure 7
Recorded signals at Ports 1 and 2 for the initial position ofA0.The two signals are distorted in the same way by the Tx and Rx components and the antennas. For these pulses, the signalsS1t and S2t, at Port 1 and Port 2, respectively, can be described by a sine carrier modulated by a Gaussian pulse [12] as
(4)S1t=Acos2πf0te−t/T′2,S2t=Acos2πf0t−Δte−t−Δt/T′2,where A is the signal magnitude, f0 is the signal carrier frequency, Δt=T2−T1 is the delay for the Path-dif, and T′ is the distorted pulse duration.With an azimuth angle close to 90°, the Path-dif to measure is too small. In addition, the duration of the received pulse is much longer than the time difference (T’≫Δt) when the path difference is very small (as shown in Figure 8).Figure 8
TheT′, Δt parameter definition.The path difference between two received signals is estimated through the corresponding time differenceΔt, obtained by correlating these two signals on the two receiving chains.By applying the cross-correlation functionCS1S2Δt to the two received signals S1t and S2t, we obtain
(5)CS1S2Δt=A2T∫0Tcos2πf0tcos2πf0t−Δt⏟Bte−tT′2e−t−ΔtT′2⏟Ctdt.The duration analysis windowT is equal to the initial pulse width (Figure 3(a)), here 2 ns.For a small path difference andT, Δt≪T′, the coefficients Bt and Ct can be written as
(6)Bt=cos2πf0Δt1+cos4πf0t2+sin2πf0Δtsin4πf0t2,Ct=e−2t2/T′2−Δt2/T′2+2Δt.t/T′2≈1.So, the cross-correlation functionCS1S2Δt becomes
(7)CS1S2Δt≈A2T∫0TBtdt≈A22cos2πf0Δt,which is considered as the Phase Correlation (PC) method directly related to the azimuth α through Δt=T2−T1 according to Equation (3).


## 5. Experimental Results

As proof of concept, we compare for each position ofA0 the results of the azimuth angle determination obtained by the conventional ED method [13] to the PC method with the configuration described in Figure 5. The ED method starts by partitioning the received signal, over the time, by blocks. Next, to estimate the ToA of the received signal, the block carrying the maximum energy is searched. So, with this method, the resolution is led by the size of blocks, here equal to 1 ns, where the minimum size is fixed by the minimum energy able to be detected.Therefore, the minimum path difference that the ED method can detect is 30 cm. Thus, it is not able to detect a path difference in the order of 5.7 cm which corresponds to the maximum Path-dif obtained by this configuration (atp−15 and p15). On the other hand, the minimum path difference that the PC method can detect is determined by the sampling frequency, and therefore, it is able to detect a path difference of 1.5 cm when Fs=20GHz and 0.2 cm when Fs=160GHz. This is directly reflected on the azimuth angle estimation since the path difference and the azimuth angle are related according to Equation (2). Note that, Fs=160GHz is used only to show the theoretical limit of the method (ideal case).In Figure9, we present the azimuth angle versus the different positions of A0 for Fs equal to 160 GHz (a) and 20 GHz (b). The actual angle is compared to the ED and PC method estimation. We show that it is impossible to determine the azimuth angle α for short Path-dif with the ED method because the effective frequency bandwidth is reduced due to the time distortion of the pulse.Figure 9
Azimuth angle estimation Vs Positions ofA0.
(a)
Sampling frequencyFs=160GHz (oversampling mode)(b)
Sampling frequencyFs =20 GHzThis becomes possible using the PC method in which the error is driven by the sampling frequencyFs. For instance, the error is less than 1° for Fs=160GHz (oversampling mode) and reaches 2° for Fs=20GHz.


## 6. Conclusion

In this paper, we have shown that the measurement accuracy of the azimuth angle by a 2D interferometric indoor localization system is strongly improved. By jointly exploiting an IR-UWB signal, the distortions of this signal, and a Phase Correlation method, the improvement achieves an error of 1° without increasing the frequency bandwidth even for angles producing very small Path-dif. This method can be extended to measure the elevation angle by adding a second Rx-Chain architecture on an orthogonal axis to the first one.



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*Source: 2603861-2020-06-10.xml*