# A New Capacitor-Less Buck DC-DC Converter for LED Applications

Authors: Munir Al-Absi; Zainulabideen Khalifa; Alaa Hussein
Journal: Active and Passive Electronic Components
 (2017)

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## Abstract

In this paper, a new capacitor-less DC-DC converter is proposed to be used as a light emitting diode (LED) driver. The design is based on the utilization of the internal capacitance of the LED to replace the smoothing capacitor. LED lighting systems usually have many LEDs for better illumination that can reach multiple tens of LEDs. Such configuration can be utilized to enlarge the total internal capacitance and hence minimize the output ripple. Also, the switching frequency is selected such that a minimum ripple appears at the output. The functionality of the proposed design is confirmed experimentally and the efficiency of the driver is 85% at full load.


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## Body

## 1. Introduction

Light emitting diodes (LEDs) are starting to experience widespread usage in many lighting applications. LEDs are replacing florescent lighting because of the LEDs’ advantages compared to the florescent lamps. These advantages are mainly lower power consumption and longer life expectancy. However, commercial LED drivers limit the life expectancy of the LED lighting system to around one-fifth of the lifetime of the LED itself. The main reason of the driver short lifetime is the smoothing capacitor at the output. This is due to leakage in this capacitor, and hence this causes degradation in the driver performance with time. Several works on electrolytic capacitor-less LED drives have been presented to maximize the overall lifetime of the LED system and the recent states of the art are given in [1–7]. In [1], a current injection approach is used. In [2–7] several single-stage topologies using multiple switches or using shared switch techniques are presented. Most of the works presented require relatively complicated power circuits or current controlled technique to reduce the size of the energy storage capacitor. These topologies lead to larger area and higher cost. A new design of capacitor-less driver is presented in [8]. The design used a storage capacitor Cd and a two-winding dual inductor.The major intention of this paper is to build upon the results obtained in [9] and present the mathematical model and experimental results to confirm the functionality of the design. The rest of the paper is organized as follows: Section 2 describes the proposed design. Mathematical analysis and experimental results are given in Section 3. Section 4 concludes the paper.


## 2. The Proposed Design

The proposed design is based on the well-known buck converter shown in Figure1, where the output voltage is the voltage across the load resistance RL and C0. Vpulse represents the controlling pulses generated from the control circuit. The DC output voltage is given by(1)VODC=DVin-Vds-D′Vd1+rL/RL,where Vds is the drain-to-source voltage of the MOS transistor used for switching, rL is the inductor resistance, Vd is the diode voltage drop, D is the ON duty cycle of the control pulse, and D′is the OFF duty cycle of the pulse.Figure 1
Buck DC-DC converter.The inductorL and the smoothing capacitor C0 will average the pulses passing through Q1 causing ripples on the load. The ripple voltage will be affected by the duty cycle, the switching frequency, the inductance, the internal resistance of the smoothing capacitor ESR, and the value of the smoothing capacitor.The approximate voltage ripples assuming linear models and a small ripple voltage are given by [10](2)ΔVr=Vin-Vo+Vds+VrLLfs×D18Cofs+ESR,where fs is the switch frequency of Vpulse, L is the inductor, VrL is the voltage across the inductor resistance, and ESR is the capacitor series resistor.The proposed design is a modified version of the design in Figure1 and is shown in Figure 2, where the load is an array of LEDs, as it is the case in all commercially available LED lamps. The internal capacitance of the LED array will act as a smoothing capacitor if a proper switching frequency and duty cycle are chosen, and hence no external smoothing capacitor is needed.Figure 2
The proposed capacitor-less buck DC-DC converter.


## 3. Mathematical Analysis and Experimental Results

### 3.1. Mathematical Analysis

It is well known that the LED in conduction mode can be modeled using a resistor and an ideal diode for DC mode and a capacitor and a resistor in parallel for AC mode as shown in Figures3(a) and 3(b), respectively. The resistance rs represents the constant series contact resistance and quasineutral region resistance of the LED, rd represents the small signal resistance of the LED at certain DC current, and Cd represents the diffusion capacitance at a certain DC current. In conduction mode, rd is the reciprocal of the conductance which is equal to the DC current divided by the thermal voltage. This indicates that as the DC current increases, the value of the resistance rd will decrease. Moreover, the value of Cd also is a function of the conductance and its value will increase as the current increases [11].Figure 3
LED model in conduction mode for (a) DC mode and (b) AC mode.
(a) (b)With reference to Figure2, the DC output voltage across the LEDs is the same as in (1) with RL replaced by RLED. The LED equivalent circuits shown in Figure 3 are used in this analysis. The DC output voltage is given by(3)VODC=DVin-Vds-D′Vd1+rL/RLED,where rL is inductor resistance. The value of RLED depends on the current passing through the LED, and it can be deduced from the I-V characteristics curve of the LED shown in Figure 4. It is clear form Figure 4 that as the current increases, the value of RLED will decrease.Figure 4
TheV-I characteristics curve of a single white LED.To find the effective capacitance of the LED, the ripple current is given by(4)ΔIpp=Vin-Vo+Vds+VrLLfs×D,where ΔIpp is the ripple current through the inductor L. From Figure 2 and the model of Figure 3, the output voltage ripple is given by(5)ΔVr=ΔIpp×RLOAD=ΔIppz+rs,where z=(rd×1/8fsCd)/(rd+1/8fsCd)=rd/(1+8rdfsCd) and 1/8fsCd is the impedance of the diffusion capacitor [10].Combining (4) and (5), the output voltage ripple is given by(6)ΔVr=ΔIpprs+1gd+8fsCd,where gd=1/rd.Rewriting (6) to find the effective capacitance Cd, (7)Cd=18fs1ΔVr/ΔIpp-rs-gd.Plots of the effective capacitance as a function of the LED current for different frequencies are shown in Figure 5. It is evident from the figure that the effective capacitance at 200 kHz is high since the impedance of the capacitance is much smaller than that of the dynamic resistance.Figure 5
Plot of the effective capacitanceCd versus the load current.In the AC model of Figure3, the behavior of rd and Cd gives an indication that as the DC current increases, the ripple voltage will decrease, which is another parameter that can be controlled and affect the ripple voltage. This fact is supported by the experimental results we have carried out and it is explained in the next section.It is important to point out that the value ofCd is linearly changing with the DC current only in strong conduction mode [12]. However, during the OFF period in the switching buck converter pulse, the LED internal resistance will draw the stored charge and the output voltage will decrease. If the OFF period is long enough, the value of the diffusion capacitor will be very small causing a sharp drop in the output voltage that might cause flicker in the LED light.


### 3.2. Experimental Results

The circuit shown in Figure2 was connected in the laboratory using off-the-shelf components to test the proposed design experimentally. The LED used is the sum of 3 series packages of 11 parallel LEDs per package giving a total of 33 LEDs. The output voltage is measured across the LED packages. The components used are as follows: L is an inductor of 470 uH, Q1 is an N-MOS power transistor BUZ71, Vpulse is the switching control pulse with an amplitude of 10 V, and D1 is a silicon fast switching diode 1N914. The inductor’s series resistance was measured and its value was approximately 4 Ω. It was assumed that the AC source was rectified and provided a DC output called Vin with nominal voltage of 35 V. The LED’s I-V characteristics shown in Figure 4 have been used to extract the value of RLED for different DC current values.The behavior of the circuit was studied by varying the duty cycle ofVpulse from 18% to 44% at three different frequencies (100 kHz, 150 kHz, and 200 kHz). The maximum duty cycle was set to 44% because this duty cycle will produce the maximum LED current. The DC output and ripple voltage are plotted in Figure 6. As is clear from the figure, as the duty cycle increases, the DC output voltage increases. The ripple voltage decreased with the increase in frequency.Figure 6
The output DC (Vo) and ripple (Vr) voltage versus the duty cycle for different frequencies.From Figure6, the DC voltage is changing linearly with the duty cycle for D > 30%. Also, it is clear that, for duty cycle greater than 30%, the error is less than 3%. The deviation between theoretical and experimental results is shown in Figure 7. It is evident from the plot that a designer should select the switching pulse duty cycle to be greater than 30% to minimize the error and a higher frequency to minimize the ripple voltage.Figure 7
The %error in the experimental results with respect to the theory versus the duty cycle.If the voltage across the LED reached below a certain value, there will be no diffusion capacitor, and the LED’s voltage will drop logarithmically, causing the large error shown in Figure7. This value can be estimated from the knees of each curve and depends on the forward current as well, since it depends on how deep the LED is in the conduction region. Figures 8 and 9 show the ripple voltage at 100 kHz with duty cycle of 18% and 40%, respectively. The nonlinearity is clearly shown in Figure 8, where the OFF period was long enough to drive the LED to the weak conduction region while the ripple of Figure 9 is almost linear. It is clear that the ripple is linear for higher duty cycle.Figure 8
Plot of ripple voltage versus time at 100 kHz andD = 18%.Figure 9
Plot of ripple voltage versus time at 100 kHz andD = 40%.To investigate the changes on the DC output voltages and ripple, the frequency was swept from 50 kHz to 300 kHz at a fixed duty cycle of 40%, and the output was probed. The result is shown in Figure10. It is clear that the ripple voltage is decreasing as the frequency increases and the DC voltage is almost constant. The minimum ratio of ripple voltage to DC voltage is around 1.4% and it can be decreased further by increasing the frequency.Figure 10
The output DC (Vo) and ripple (Vr) voltage versus frequency.Efficiency is an important factor in a LED driver. The efficiency was found by measuring the DC output voltage, the output current, the DC input voltage, and the input current for each duty cycle for different frequencies. Experimental results displayed in Figure11 show that the average efficiency is 85%. The efficiency can be further improved using an inductor with smaller internal resistance and a transistor with smaller ON resistance.Figure 11
The efficiency versus the duty cycle at different frequencies.Because of the slight changes in the DC output voltage, the efficiency is barely changing with the change of the frequency, as shown in Figure12. The average of the efficiency over the frequency range was about 88%. Increasing the frequency further will lead to smaller ripple voltages and smaller components for better integration. However, increasing the switching frequency will reduce the efficiency of the drive because of the switching power loss for light loads [12]. As for LED lighting applications, the LED load needs to draw high current specially when using a capacitor-less drive. This is because it is better to use many parallel LEDs for higher summation of LED capacitance, which gives this method one more advantage.Figure 12
The efficiency versus frequency.


## 3.1. Mathematical Analysis

It is well known that the LED in conduction mode can be modeled using a resistor and an ideal diode for DC mode and a capacitor and a resistor in parallel for AC mode as shown in Figures3(a) and 3(b), respectively. The resistance rs represents the constant series contact resistance and quasineutral region resistance of the LED, rd represents the small signal resistance of the LED at certain DC current, and Cd represents the diffusion capacitance at a certain DC current. In conduction mode, rd is the reciprocal of the conductance which is equal to the DC current divided by the thermal voltage. This indicates that as the DC current increases, the value of the resistance rd will decrease. Moreover, the value of Cd also is a function of the conductance and its value will increase as the current increases [11].Figure 3
LED model in conduction mode for (a) DC mode and (b) AC mode.
(a) (b)With reference to Figure2, the DC output voltage across the LEDs is the same as in (1) with RL replaced by RLED. The LED equivalent circuits shown in Figure 3 are used in this analysis. The DC output voltage is given by(3)VODC=DVin-Vds-D′Vd1+rL/RLED,where rL is inductor resistance. The value of RLED depends on the current passing through the LED, and it can be deduced from the I-V characteristics curve of the LED shown in Figure 4. It is clear form Figure 4 that as the current increases, the value of RLED will decrease.Figure 4
TheV-I characteristics curve of a single white LED.To find the effective capacitance of the LED, the ripple current is given by(4)ΔIpp=Vin-Vo+Vds+VrLLfs×D,where ΔIpp is the ripple current through the inductor L. From Figure 2 and the model of Figure 3, the output voltage ripple is given by(5)ΔVr=ΔIpp×RLOAD=ΔIppz+rs,where z=(rd×1/8fsCd)/(rd+1/8fsCd)=rd/(1+8rdfsCd) and 1/8fsCd is the impedance of the diffusion capacitor [10].Combining (4) and (5), the output voltage ripple is given by(6)ΔVr=ΔIpprs+1gd+8fsCd,where gd=1/rd.Rewriting (6) to find the effective capacitance Cd, (7)Cd=18fs1ΔVr/ΔIpp-rs-gd.Plots of the effective capacitance as a function of the LED current for different frequencies are shown in Figure 5. It is evident from the figure that the effective capacitance at 200 kHz is high since the impedance of the capacitance is much smaller than that of the dynamic resistance.Figure 5
Plot of the effective capacitanceCd versus the load current.In the AC model of Figure3, the behavior of rd and Cd gives an indication that as the DC current increases, the ripple voltage will decrease, which is another parameter that can be controlled and affect the ripple voltage. This fact is supported by the experimental results we have carried out and it is explained in the next section.It is important to point out that the value ofCd is linearly changing with the DC current only in strong conduction mode [12]. However, during the OFF period in the switching buck converter pulse, the LED internal resistance will draw the stored charge and the output voltage will decrease. If the OFF period is long enough, the value of the diffusion capacitor will be very small causing a sharp drop in the output voltage that might cause flicker in the LED light.


## 3.2. Experimental Results

The circuit shown in Figure2 was connected in the laboratory using off-the-shelf components to test the proposed design experimentally. The LED used is the sum of 3 series packages of 11 parallel LEDs per package giving a total of 33 LEDs. The output voltage is measured across the LED packages. The components used are as follows: L is an inductor of 470 uH, Q1 is an N-MOS power transistor BUZ71, Vpulse is the switching control pulse with an amplitude of 10 V, and D1 is a silicon fast switching diode 1N914. The inductor’s series resistance was measured and its value was approximately 4 Ω. It was assumed that the AC source was rectified and provided a DC output called Vin with nominal voltage of 35 V. The LED’s I-V characteristics shown in Figure 4 have been used to extract the value of RLED for different DC current values.The behavior of the circuit was studied by varying the duty cycle ofVpulse from 18% to 44% at three different frequencies (100 kHz, 150 kHz, and 200 kHz). The maximum duty cycle was set to 44% because this duty cycle will produce the maximum LED current. The DC output and ripple voltage are plotted in Figure 6. As is clear from the figure, as the duty cycle increases, the DC output voltage increases. The ripple voltage decreased with the increase in frequency.Figure 6
The output DC (Vo) and ripple (Vr) voltage versus the duty cycle for different frequencies.From Figure6, the DC voltage is changing linearly with the duty cycle for D > 30%. Also, it is clear that, for duty cycle greater than 30%, the error is less than 3%. The deviation between theoretical and experimental results is shown in Figure 7. It is evident from the plot that a designer should select the switching pulse duty cycle to be greater than 30% to minimize the error and a higher frequency to minimize the ripple voltage.Figure 7
The %error in the experimental results with respect to the theory versus the duty cycle.If the voltage across the LED reached below a certain value, there will be no diffusion capacitor, and the LED’s voltage will drop logarithmically, causing the large error shown in Figure7. This value can be estimated from the knees of each curve and depends on the forward current as well, since it depends on how deep the LED is in the conduction region. Figures 8 and 9 show the ripple voltage at 100 kHz with duty cycle of 18% and 40%, respectively. The nonlinearity is clearly shown in Figure 8, where the OFF period was long enough to drive the LED to the weak conduction region while the ripple of Figure 9 is almost linear. It is clear that the ripple is linear for higher duty cycle.Figure 8
Plot of ripple voltage versus time at 100 kHz andD = 18%.Figure 9
Plot of ripple voltage versus time at 100 kHz andD = 40%.To investigate the changes on the DC output voltages and ripple, the frequency was swept from 50 kHz to 300 kHz at a fixed duty cycle of 40%, and the output was probed. The result is shown in Figure10. It is clear that the ripple voltage is decreasing as the frequency increases and the DC voltage is almost constant. The minimum ratio of ripple voltage to DC voltage is around 1.4% and it can be decreased further by increasing the frequency.Figure 10
The output DC (Vo) and ripple (Vr) voltage versus frequency.Efficiency is an important factor in a LED driver. The efficiency was found by measuring the DC output voltage, the output current, the DC input voltage, and the input current for each duty cycle for different frequencies. Experimental results displayed in Figure11 show that the average efficiency is 85%. The efficiency can be further improved using an inductor with smaller internal resistance and a transistor with smaller ON resistance.Figure 11
The efficiency versus the duty cycle at different frequencies.Because of the slight changes in the DC output voltage, the efficiency is barely changing with the change of the frequency, as shown in Figure12. The average of the efficiency over the frequency range was about 88%. Increasing the frequency further will lead to smaller ripple voltages and smaller components for better integration. However, increasing the switching frequency will reduce the efficiency of the drive because of the switching power loss for light loads [12]. As for LED lighting applications, the LED load needs to draw high current specially when using a capacitor-less drive. This is because it is better to use many parallel LEDs for higher summation of LED capacitance, which gives this method one more advantage.Figure 12
The efficiency versus frequency.


## 4. Conclusion

A new approach to designing capacitor-less buck DC-DC converter was developed and tested. The proposed single switch circuit is able to reduce the ripple in a compact form and can be extended to any other LED configuration. The design’s mathematical model was developed based on experimental verification. The efficiency of the driver is 85% and we expect the lifetime to be much higher than existing drives, as there is no capacitor in the switching path of the driver.



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*Source: 2365848-2017-01-17.xml*