# Wideband Polarization Conversion Metasurface for RCS Reduction of Antennas

Authors: Tao Hong; Ke Peng; Yue Gu; Wen Jiang; Shuxi Gong
Journal: International Journal of Antennas and Propagation
 (2018)

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## Abstract

Polarization conversion metasurface (PCM) with wide operating band and high polarization conversion ratio is proposed for antenna radar cross-section (RCS) reduction. A 3rd-order quadrate fractal structure (QFS) is designed as the PCM element that the polarization conversion ratio is greater than 80% from 10.45 GHz to 32.15 GHz (relative bandwidth of 101.9%). The PCM is applied in the RCS reduction of microstrip antennas by chessboard-like arrangement on the antenna. The performances of the proposed PCM and antenna are studied by measurement and simulation. The results show that, with the radiation performance hold, the monostatic RCS of the proposed antenna is obviously reduced from 8 GHz to 28 GHz which completely covers the operating band of the antenna.


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## Body

## 1. Introduction

With the rapid development of new system of radar, the stealth characteristics of various military carriers such as aircrafts and warships are getting more and more attention. Low radar cross-section (RCS) property of the carrier can reduce the ability of the enemy’s radar to detect the target, thereby improving the battlefield viability and penetration ability of one’s own goals. Antennas are essential for a variety of radio equipment, and they are responsible for transmitting and receiving electromagnetic waves. In a complex electromagnetic environment, how to improve the carrier stealth performance while maintaining the normal work of the antenna is a difficult task, which is becoming a hot spot.The working principle of the checkerboard surfaces is that the scattering field of the adjacent checkerboard blocks is cancelled because the amplitude is the same and the phase difference is180° [1–6]. A wider 10 dB RCS reduction bandwidth of 60% is obtained by combining two different types of electromagnetic band gap (EBG) structures for the square and hexagonal checkerboard surfaces [1]. Checkerboard surfaces consisting of two different EBG structures can realize 10 dB RCS reduction bandwidths of 61% and 24% [2]. In [5], the RCS is reduced by more than 10 dB in the band of 9.4 GHz–23.28 GHz. The size adjustment metasurface (SA-MS) is composed of a wideband polarization conversion surface and a partially reflecting surface (PRS), which obtained a wideband RCS reduction in the frequency range of 9 GHz–17 GHz [6].In the past few years, some research activities on the RCS reduction of antenna with polarization conversion characteristics have been reported, which is acquired by polarization conversion metasurface (PCM). The split-ring sheet PCM can realize 5 dB RCS reduction in a wide range from 8.6 GHz to 24.5 GHz, and the relative bandwidth reaches up to 96% [7]. In 2016, Liu et al. loaded 45° angle symmetric split-ring resonators around a microstrip antenna, achieving RCS reduction in 4.2 GHz, 6.75 GHz, 9 GHz, and 12 GHz bands [8]. They proposed a new PCM that was placed on the surface of the slot array antenna, reducing the monostatic RCS and preserving the radiation characteristics [9]. The proposed metasurface has a remarkable (5 dB) monostatic RCS reduction characteristic from 8.6 GHz to 24.5 GHz [10]. In [11], an ultrawideband dual-patch PRS is presented to widen the polarization rotation bandwidth from 49% to 97% with a high polarization conversion ratio (PCR) of 96%, and 10 dB RCS reduction is achieved over 98%. A microstrip antenna array with a metasurface based on size-adjustable unit cells is designed, which is capable of achieving a RCS reduction larger than 5 dB from 6.2 GHz to 27.3 GHz (126.0% frequency bandwidth) [12].In order to improve the bandwidth and polarization conversion efficiency of polarization conversion metasurfaces, novel polarization devices have been proposed in many studies. An ultrathin chiral metamaterial slab stacked with twisted complementary split-ring resonators realized conversion efficiency of up to 96% covering a bandwidth of 24% of the central wavelength [13]. Shi et al. realized the polarization rotation modulation of the transmitted waves in three frequency bands of 9.82 GHz, 11.39 GHz, and 13.37 GHz by loading four symmetrical rotating open rings on both sides of the dielectric substrate [14]. Chen et al. used an asymmetric double-aperture resonant ring structure to achieve 80% reflection-wave polarization rotation modulation in the band from 7 GHz to 20 GHz [15]. The polarization conversion metasurface of the open-elliptical ring resonator is capable of achieving the polarization rotation efficiency of greater than 85% over a frequency range of 104.5% of the relative bandwidth [16]. An ultrathin wideband polarization conversion composing of arrays of oval ring pattern obtained a polarization conversion ratio (PCR) of over 68.6% from 8.0 GHz to 18.0 GHz [17]. An ultrawideband and high-performance polarization converter that makes use of a double V-shaped metasurface is proposed, with a mean PCR of 90% from 12 GHz to 27.9 GHz [18]. The polarization conversion metasurfaces consist of a dielectric substrate sandwiched between double split-ring resonators (DSRR), disk resonators, and a ground plane, whose polarization conversion ratio is above 94% for the Ku-band and 90% (11.5 GHz to 20 GHz) for the Ka-band (28.8 GHz to 34 GHz) [19].In this paper, an ultrawideband and high-efficiency PCM is proposed. By a novel quadrate fractal structure element, the operating band from 10.45 GHz to 32.15 GHz is achieved. The proposed PCM is applied in the RCS reduction of a microstrip antenna. The validity in the RCS reduction is proved by both measurements and simulations.


## 2. Design of PCM

### 2.1. Design of the PCM Unit Cell

The geometry of the PCM unit is shown in Figure1. The unit is composed of three layers: quadrate fractal structure (QFS) (top layer), metal plane (bottom layer), and substrate with W = 6 mm in the side length (intermediate layer). The QFS consists of three squares with side lengths L1=2.2 mm, L2=1 mm, and L3=0.5 mm, respectively. Square patches are connected by a strip with D=0.1 mm in width. The intermediate layer is a substrate with a relative permittivity of 2.62 and H=2 mm in thickness.Figure 1
Geometry of the PCM unit cell: (a) Top view; (b) side view.
(a)
(b)All the simulations in this study are done with the Ansys HFSS software based on the finite element method (FEM). By arranging the units periodically on a plane, a PCM is obtained whose reflection and polarization conversion performances are studied. In order to find out the performances of the element in different iterations, the 2nd-order, 3rd-order, and 4th-order fractal elements are simulated as shown in Figure2. From the reflection coefficient curves, it can be observed that the curve of the 2nd-order fractal structure is not smooth enough to provide a stable wideband PCR curve. In terms of the operating bandwidth and smoothness, the 3rd-order fractal structure is obviously a better choice than the 4th-order one.Figure 2
Discussion on the iteration of the QFS.Based on the discussion above, the 3rd-order QFS is used and the performances are shown in Figure3 when the incident waves are x-polarized (the same as y-polarized due to the symmetric structure of QFS). According to the red and blue lines, the PCM keeps a high cross-polarized reflection coefficient when linear-polarized waves light the PCM normally. Under the condition of cross-polarization reflection coefficient great than −1 dB, the operating band of the PCM is from 10.45 GHz to 32.15 GHz (relative bandwidth of 101.9%).Figure 3
Reflection and polarization conversion performance of the PCM.Furthermore, to exhibit the performances of the PCM more visually, polarization conversion ratio is also shown in Figure3 by a black line. In the operating band of the PCM, the polarized conversion ratio is greater than 80% which means that 80% of the linear incident power is converted into the cross-polarized power. There are three peak values at 11 GHz, 22.2 GHz, and 32.6 GHz where the PCM can work with a polarization conversion ratio closing to 100%.To interpret the mechanism of the polarization conversion, the cases ofu- and v-polarization incidence are studied. As shown in Figure 4, three resonant frequency points within the operating band of the PCM can be found at 11 GHz, 22.2 GHz, and 32.6 GHz which correspond with the three peak values of the polarization conversion ratio. The surface current distributions of the QFS and ground plane at 11 GHz, 22.2 GHz, and 32.6 GHz are shown in Figure 5. The induced current generated by the QFS is opposite to that of the ground plane, which constitutes an equivalent magnetic resonator at 11 GHz. At 22.2 GHz, the direction of surface current for QFS is orthogonal to that of the ground plane, which leads to the orthogonal reflection of the electric field. When the frequency of the incident wave increases to 32.6 GHz, the induced current has the same direction as that of the ground plane, which constitutes an equivalent electric resonator.Figure 4
Copolarization reflection ofu- and v-polarized incidence: (a) u-polarized incidence; (b) v-polarized incidence.
(a)
(b)Figure 5
Current distribution on the QFS and ground plane at the resonant frequency points: (a) 11.1 GHz; (b) 22.2 GHz; (c) 32.6 GHz.
(a)
(b)
(c)


### 2.2. Mechanism of RCS Reduction

As shown in Figure6, the chessboard-like plane is divided into two regions: region I (upper right block and lower left block) and region II (upper left block and lower right block). In region I, two 5 × 5 arrays are formed by the QFS elements, while in region II, the other two 5 × 5 arrays are formed by the mirror elements of the QFS.Figure 6
Configuration of the chessboard-like plane.When the incident wave illuminates the chessboard-like plane normally, the reflected wave will be the superposition of the reflected waves from region I and region II. It is supposed that the reflected electric field from region I is(1)E¯1=A1∙ejφ1.Due to the chessboard arrangement, the reflected wave from region II is in the same amplitude and180° phase difference with that from region I. The reflected electric field from region II is
(2)E¯2=A2∙ejφ2=A1∙ejφ1±180°.WithE¯1 and E¯2, the total reflected electric field is
(3)E¯chessboard=E¯1+E¯2=A1∙ejφ1+A1∙ejφ1±180°.It can be found that the reflected wave will be too weak to be detected due to the superposition.However, the phase difference betweenE¯1 and E¯2 is not exactly 180° for most of the frequency points in the operating band. In this case, the total reflected electric field is
(4)E¯chessboard=A1∙ejφ11+ejφ2−φ1.Moreover, in the metal plane, the total reflected electric field is(5)E¯metal=2A1∙ejφ1.In order to keep the reflected power in a low level, for example,(6)E¯chessboard2E¯metal2≤−10dB,then
(7)cosφ2−φ1≤−0.8.The phase difference will be(8)143°≤φ2−φ1≤217°.From (8), the reflected power will be obviously reduced when the reflected phase difference between region I and region II is 180°±30°.The monostatic RCS curves of the chessboard-like plane and perfect electric conductor (PEC) plane which are illuminated by thex-polarized and y-polarized incident waves are shown in Figure 7. When the plane is illuminated normally, the structure of the plane is all the same for both x-polarized and y-polarized incident waves. Theoretically, the same resonant performances of the plane could be obtained due to the symmetrical structure of the chessboard-like plane. Therefore, the monostatic RCS curves of the proposed antenna are almost matching between the x-polarized and y-polarized incident cases. It can be found that the reflected power is well suppressed from 6 GHz to 38GHz with a relative bandwidth of 145.5% for both x- and y-polarized incidence cases. From 7.2 GHz to 28.7 GHz, a relative bandwidth of 119.7%, the RCS of the chessboard-like plane is reduced for more than 4 dBsm.Figure 7
Monostatic RCS of the chessboard-like plane and PEC plane for normal incidence: (a)x-polarized incidence; (b) y-polarized incidence.
(a)
(b)


## 2.1. Design of the PCM Unit Cell

The geometry of the PCM unit is shown in Figure1. The unit is composed of three layers: quadrate fractal structure (QFS) (top layer), metal plane (bottom layer), and substrate with W = 6 mm in the side length (intermediate layer). The QFS consists of three squares with side lengths L1=2.2 mm, L2=1 mm, and L3=0.5 mm, respectively. Square patches are connected by a strip with D=0.1 mm in width. The intermediate layer is a substrate with a relative permittivity of 2.62 and H=2 mm in thickness.Figure 1
Geometry of the PCM unit cell: (a) Top view; (b) side view.
(a)
(b)All the simulations in this study are done with the Ansys HFSS software based on the finite element method (FEM). By arranging the units periodically on a plane, a PCM is obtained whose reflection and polarization conversion performances are studied. In order to find out the performances of the element in different iterations, the 2nd-order, 3rd-order, and 4th-order fractal elements are simulated as shown in Figure2. From the reflection coefficient curves, it can be observed that the curve of the 2nd-order fractal structure is not smooth enough to provide a stable wideband PCR curve. In terms of the operating bandwidth and smoothness, the 3rd-order fractal structure is obviously a better choice than the 4th-order one.Figure 2
Discussion on the iteration of the QFS.Based on the discussion above, the 3rd-order QFS is used and the performances are shown in Figure3 when the incident waves are x-polarized (the same as y-polarized due to the symmetric structure of QFS). According to the red and blue lines, the PCM keeps a high cross-polarized reflection coefficient when linear-polarized waves light the PCM normally. Under the condition of cross-polarization reflection coefficient great than −1 dB, the operating band of the PCM is from 10.45 GHz to 32.15 GHz (relative bandwidth of 101.9%).Figure 3
Reflection and polarization conversion performance of the PCM.Furthermore, to exhibit the performances of the PCM more visually, polarization conversion ratio is also shown in Figure3 by a black line. In the operating band of the PCM, the polarized conversion ratio is greater than 80% which means that 80% of the linear incident power is converted into the cross-polarized power. There are three peak values at 11 GHz, 22.2 GHz, and 32.6 GHz where the PCM can work with a polarization conversion ratio closing to 100%.To interpret the mechanism of the polarization conversion, the cases ofu- and v-polarization incidence are studied. As shown in Figure 4, three resonant frequency points within the operating band of the PCM can be found at 11 GHz, 22.2 GHz, and 32.6 GHz which correspond with the three peak values of the polarization conversion ratio. The surface current distributions of the QFS and ground plane at 11 GHz, 22.2 GHz, and 32.6 GHz are shown in Figure 5. The induced current generated by the QFS is opposite to that of the ground plane, which constitutes an equivalent magnetic resonator at 11 GHz. At 22.2 GHz, the direction of surface current for QFS is orthogonal to that of the ground plane, which leads to the orthogonal reflection of the electric field. When the frequency of the incident wave increases to 32.6 GHz, the induced current has the same direction as that of the ground plane, which constitutes an equivalent electric resonator.Figure 4
Copolarization reflection ofu- and v-polarized incidence: (a) u-polarized incidence; (b) v-polarized incidence.
(a)
(b)Figure 5
Current distribution on the QFS and ground plane at the resonant frequency points: (a) 11.1 GHz; (b) 22.2 GHz; (c) 32.6 GHz.
(a)
(b)
(c)


## 2.2. Mechanism of RCS Reduction

As shown in Figure6, the chessboard-like plane is divided into two regions: region I (upper right block and lower left block) and region II (upper left block and lower right block). In region I, two 5 × 5 arrays are formed by the QFS elements, while in region II, the other two 5 × 5 arrays are formed by the mirror elements of the QFS.Figure 6
Configuration of the chessboard-like plane.When the incident wave illuminates the chessboard-like plane normally, the reflected wave will be the superposition of the reflected waves from region I and region II. It is supposed that the reflected electric field from region I is(1)E¯1=A1∙ejφ1.Due to the chessboard arrangement, the reflected wave from region II is in the same amplitude and180° phase difference with that from region I. The reflected electric field from region II is
(2)E¯2=A2∙ejφ2=A1∙ejφ1±180°.WithE¯1 and E¯2, the total reflected electric field is
(3)E¯chessboard=E¯1+E¯2=A1∙ejφ1+A1∙ejφ1±180°.It can be found that the reflected wave will be too weak to be detected due to the superposition.However, the phase difference betweenE¯1 and E¯2 is not exactly 180° for most of the frequency points in the operating band. In this case, the total reflected electric field is
(4)E¯chessboard=A1∙ejφ11+ejφ2−φ1.Moreover, in the metal plane, the total reflected electric field is(5)E¯metal=2A1∙ejφ1.In order to keep the reflected power in a low level, for example,(6)E¯chessboard2E¯metal2≤−10dB,then
(7)cosφ2−φ1≤−0.8.The phase difference will be(8)143°≤φ2−φ1≤217°.From (8), the reflected power will be obviously reduced when the reflected phase difference between region I and region II is 180°±30°.The monostatic RCS curves of the chessboard-like plane and perfect electric conductor (PEC) plane which are illuminated by thex-polarized and y-polarized incident waves are shown in Figure 7. When the plane is illuminated normally, the structure of the plane is all the same for both x-polarized and y-polarized incident waves. Theoretically, the same resonant performances of the plane could be obtained due to the symmetrical structure of the chessboard-like plane. Therefore, the monostatic RCS curves of the proposed antenna are almost matching between the x-polarized and y-polarized incident cases. It can be found that the reflected power is well suppressed from 6 GHz to 38GHz with a relative bandwidth of 145.5% for both x- and y-polarized incidence cases. From 7.2 GHz to 28.7 GHz, a relative bandwidth of 119.7%, the RCS of the chessboard-like plane is reduced for more than 4 dBsm.Figure 7
Monostatic RCS of the chessboard-like plane and PEC plane for normal incidence: (a)x-polarized incidence; (b) y-polarized incidence.
(a)
(b)


## 3. Antenna RCS Reduction Based on PCM

The proposed PCM is applied in the RCS reduction of the microstrip antenna in this section. The configuration of the proposed antenna is shown in Figure8. It consists of radiation patch, ground plane, and QFSs in chessboard arrangement. The QFSs and radiation patch are on the same side of the substrate with a relative permittivity of 2.62. Behind the radiation patch, a cavity is inserted into the substrate to improve the impendence matching of the antenna. The ground plane is on the other side of the substrate. The sizes of the proposed antenna are shown as follows: P = 65 mm, H = 2 mm, R = 1.2 mm, D = 17 mm, W = 8 mm, and G = 2.2 mm. As a reference, another antenna is designed without QFSs. The prototypes of the proposed and reference antennas are shown in Figure 9.Figure 8
Configuration of the proposed antenna: (a) top view; (b) side view.
(a)
(b)Figure 9
Prototypes of the proposed and reference antennas.As shown in Figure10, the |S11| curves of the proposed and reference antennas fit well which means that the antennas share the same operating band. Under the condition of |S11 |≤−10 dB, the measured operating bands of the proposed and reference antennas are from 13.04 GHz to 14.97 GHz (relative bandwidth of 13.8%) and from 13.17 GHz to 14.89 GHz (relative bandwidth of 12.3%), respectively. However, frequency shifts appear between the simulated and measured curves. The frequency shifts, which are prevalent in antenna engineering, are caused by the errors in the fabrication and the electrical parameters of the substrate.Figure 10
Measured and simulated |S11| of the antennas.Figure11 is the normalized radiation patterns of the proposed and reference antennas at 14 GHz. The measurements are carried out in the anechoic chamber. The curves are in good agreement with the simulated ones. On the working direction (θ=0°), the gains of the proposed and reference antennas are 7.13 dBi and 6.2 dBi. The radiation patterns and gains show that the proposed antenna has similar radiation performances with the reference antenna. The mismatching between the curves is caused by the coupling between the PCM element and the antenna radiator.Figure 11
Normalized radiation patterns of the proposed and reference antenna at 14 GHz: (a)xz-plane; (b) yz-plane.
(a)
(b)The monostatic RCS of the proposed and reference antennas is studied when the incident plane waves illuminate the antennas normally. It can be found from Figure12 that, with the radiation performance hold, the RCS of the proposed antenna is obviously lower than that of the reference antenna from 8 GHz to 28 GHz for both the x- and y-polarized incidence. Especially in the operating band of the proposed antenna, the RCS is reduced by more than 6.8 dB for the x-polarized incidence and 7.7 dB for the y-polarized incidence.Figure 12
Monostatic RCS of the proposed and reference antennas for normal incidence: (a)x-polarized incidence; (b) y-polarized incidence.
(a)
(b)


## 4. Conclusion

Polarization conversion metasurface (PCM) with wide operating band and high polarization conversion ratio is proposed in this paper. The proposed PCM element is designed with a 3rd-order quadrate fractal structure. The polarization conversion ratio is greater than 80% from 10.45 GHz to 32.15 GHz. The performances of the proposed PCM and antenna are studied by measurement and simulation. The results show that, with the radiation performance hold, the monostatic RCS the proposed antenna is obviously reduced from 8 GHz to 28 GHz which completely covers the operating band of the antenna.



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*Source: 2308643-2018-09-27.xml*