# Backward Surface Wave Propagation and Radiation along a One-Dimensional Folded Cylindrical Helix Array

Authors: Bin Xu; Yang Li
Journal: International Journal of Antennas and Propagation
 (2015)

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## Abstract

Wave propagation along a closely spaced folded cylindrical helix (FCH) array is investigated for the purpose of designing compact array for energy transport and antenna radiation. It is found that the height of this surface wave guiding structure can be decreased from 0.24λ0 to 0.06λ0 by replacing the monopole element with the FCH. Both the propagation constant and the mode distribution of the dominant wave mechanism are extracted by ESPRIT algorithm, which indicates that a backward propagating surface wave is supported by the array structure. A compact backfire FCH antenna array is designed and measured based on the identified dominant wave mechanism.


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## Body

## 1. Introduction

Wave propagation and radiation along a one-dimensional metal wire array has long been of interest since the invention of the Yagi-Uda antenna [1]. With carefully selected monopole wire height (0.2 to 0.25λ0, withλ0 being the free space wavelength) and spacing (0.2 to 0.35λ0), a surface wave with an optimum phase velocity can be supported by the structure and can be radiated in the end-fire direction [2]. More recently, there is an emerging interest in minimizing the size of the array for two important applications: electromagnetic (EM) energy transport and compact antenna array design. It was found in [3] that the transmission loss of EM energy along a 1D metal rod array is smaller than 1.5 dB/λ0, which can be attributed to the strong coupling between closely spaced rods (0.054λ0). For the second application, a closely spaced, multiple-element parasitic antenna array was designed and implemented, with its interelement spacing being as small as 0.02λ0 [4].In spite of the above success in reducing the spacing between wires, there still remains a challenge to minimize the height of each array element. It was found that the height of metal wire should be close to a quarter-wavelength to ensure the dominant surface wave is strongly excited. One idea to minimize the element size is to substitute the metal wire with electrically small elements such as a folded spherical helix (FSH) [5] or a folded cylindrical helix (FCH) [6], the size of which can be as small as 0.06λ0. The effects of mutual coupling between two closely spaced FSHs or FCHs have been studied recently for wireless power transfer applications [7, 8]. However, wave propagation along a 1D closely spaced array with electrically small element is not well understood and still needs to be investigated. Previously we have simulated surface wave propagation along a 1D FCH array and compared the results with that of a 1D metal cut wire array [9]. In this paper, we extend our study to simulate and measure surface wave propagation and radiation along a 1D closely spaced FCH array.The paper is organized as follows: in Section2, a 21-element FCH array is first designed and fabricated. Broadband transmission data and near electric field distributions are simulated and measured along the array. In Section 3, the dominant propagation mechanism and its associated propagation characteristics, such as propagation constant and mode distribution, are extracted using a super resolution estimation algorithm. A parametric study is performed to figure out correlation between the propagation constant and array geometrical parameters. In Section 4, a compact backfire parasitic antenna array is designed based on the identified dominant wave mechanism. Both simulation and measurement results are presented. Section 5 concludes the paper.


## 2. Wave Propagation along a 1D FCH Array

First, a single 4-arm FCH element centered at 400 MHz is designed by using formulas provided in [6]. The helix radius R, height H, and number of turns are 0.0317 m, 0.047 m, and 1, respectively. The height of the folded helix corresponds to 0.063λ0, which is much shorter than that of a quarter-wavelength monopole antenna. Next, 21 identical elements are placed along a straight line in the y-axis to form the FCH array. The interelement spacing S is equal to 0.08 m, corresponding to 0.11λ0 at 400 MHz. Figures 1(a) and 1(b) show the simulation and measurement setup of the FCH array. While a finite sized metal ground plane is used in the measurement, an infinitely large perfect electric conductor (PEC) ground is assumed in the simulation to save computational time. A voltage source is placed at the bottom of the left-most element and a field probe is moved in between parasitic elements to sample the near electric fields at the ground plane level for different frequencies. Numerical software FEKO [10] is used for simulation and a vector network analyzer (Agilent PNL N5230C) is applied for measurement.Figure 1
1D folded cylindrical helix array setup: (a) simulation and (b) measurement.
(a)
(b)Figure2 compares the simulated and measured reflection coefficients S11 of the source antenna. They exhibit similar trend and both are significantly different from the sharp resonance behavior of a single FCH antenna, as presented in [6]. This is due to the strong coupling between closely spaced helixes. The resonance band in the measurement shifts downward by approximately 20 MHz comparing to the simulation data, which can be attributed to manufacturing errors.Figure 2
Simulated and measured reflection coefficients.Figures3(a) and 3(b) show the normalized transmission data for both simulations and measurements on a dB scale. The antenna mismatches have been removed by normalizing S212 to 1-S112 and 1-S222. The horizontal axis represents the frequency from 300 MHz to 500 MHz with an interval of 2.5 MHz, and the vertical axis represents the distance between transmitting and receiving antennas along the y-axis from 0.4 m to 1.6 m with a spacing of 0.08 m. As shown in Figure 3(a), the receiving field strengths are much stronger between 355 MHz and 415 MHz, and within the pass band wave propagation exhibits negligible decay along the y-axis. Outside of this pass band, field strengths are much weaker and attenuate much faster. The measurement results in Figure 3(b) show good agreement with simulation results, except the pass band shifts downward by approximately 20 MHz, similar to the above observation for Figure 2.Figure 3
Normalized transmission coefficients: (a) simulation and (b) measurement.
(a)
(b)To further reveal the wave propagation along the FCH array, we simulate the near field distributions in they-z plane at a sample frequency of 390 MHz. Figure 4 plots the normalized near electric field components Ey and Ez on a dB scale. The horizontal axis represents the distance along the y-axis from 0.4 to 1.6 m with a 0.08 m interval. The vertical axis represents height in the z direction from 0 to 0.2 m with an interval of 0.002 m. In Figure 4(a), a standing wave pattern can be clearly observed along the y direction, implying the interference between +y and -y traveling waves due to the finite size of the array. Along the z direction, the magnitude of Ey peaks at the height of the helix and decays rapidly away from the interface between the FCH and the air. A similar interference pattern can be observed in Figure 4(b) for the Ez component, except its strength is much weaker than Ey.Figure 4
Simulated near field distribution in they-z plane at 390 MHz: (a) Ey and (b) Ez.
(a)
(b)


## 3. Extraction of Dominant Wave Mechanism Using ESPRIT

To better understand how wave propagates along the 1D FCH array, we extract the dominant wave mode and its associated propagation characteristics from the above transmission and near field data. First we model the transmission data as a summation of different wave modes, each with a unique propagation constantβm, attenuation constant αm, and magnitude cm, which can then be extracted using ESPRIT algorithm. ESPRIT is a super resolution spectrum estimation algorithm which was originally developed for estimation of sinusoid signals in noise [11]. More recently, it has been successfully applied to both wave propagation and antenna radiation problems [12]. The extraction process has been explained in detail in [4] and will not be repeated here. Consider the following:(1)S21≅∑m=1Mcme-jβmy-αmy.As an example, Figures 5(a) and 5(b) plot the ESPRIT fitted magnitude and phase curves at 390 MHz by adding the first two dominant terms. The results show excellent agreement with the original simulated transmission data, and the propagation constants of the two dominant terms are found to be −2.236k0 and 2.236k0 (k0 is the free space wave number), implying the superposition of incident and reflected components of a single slow wave mode. It is found that the dominant mode is a backward traveling surface wave for the following two reasons: first, the amplitude of the mode with a propagation constant β=-2.236k0 is stronger than other modes extracted from the ESPRIT; second, the unwrapped phase increases as distance y increases, as shown in Figure 5(b), implying that the dominant mode is a backward traveling wave. The ESPRIT algorithm is also applied to the measured transmission data at 370 MHz and the comparison between original and fitted data is shown in Figures 5(c) and 5(d). We intentionally shift the frequency downward by 20 MHz to make a fair comparison between simulation and measurement, as stated in Section 2. Table 1 shows the propagation constants of the dominant backward surface wave, and the results are very similar between simulation and measurement.Table 1
Propagation parameters of the dominant mode.
Dominant mode
β
m/k0
α
m/k0
Simulation (390 MHz)
−2.236
0.0089
Measurement (370 MHz)
−2.4485
0.1584Figure 5
Comparison between original data with fitted results by ESPRIT: (a) simulated magnitude at 390 MHz; (b) simulated unwrapped phase at 390 MHz; (c) measured magnitude at 370 MHz; (d) measured unwrapped phase at 370 MHz.
(a)
(b)
(c)
(d)Furthermore, we extract the mode distribution of the dominant surface wave from the simulated near electric field data in Figures6(a) and 6(b). Figures 6(a) and 6(b) plot the extracted Ey and Ez mode distributions versus height z at 390 MHz. It can be seen that the magnitude of Ey peaks around the height of the FCH element (0.047 m) and decays exponentially away from the interface, a typical characteristic of surface wave propagation. The Ez distribution is more complicated below the interface between the FCH and the air but is similar to Ey above the FCH height. We also map out the frequency dispersion behavior of the backward traveling surface wave and show the results in Figure 7. It is seen that, except for the 20 MHz frequency shift along the horizontal axis, the values of β increase as frequency increases for both simulations and measurements.Figure 6
Normalized electric field mode distributions at 390 MHz: (a)Ey and (b) Ez.
(a)
(b)Figure 7
Extracted phase constants of simulation and measurement against frequency.Finally, a parametric study is conducted to correlate the propagation constant with array geometrical parameters. The first parameter we examined is the radiusR. Both the height and the spacing between elements are fixed. Figure 8(a) shows that β increases as R increases. The second varying parameter is the height H of the helix, as shown in Figure 8(b). The phase constant varies slightly since the total length of the helix does not change much. Finally, in Figure 8(c) we explored the effect of spacing and it was found that by increasing the interval of the adjacent element from 0.07 m to 0.1 m the propagation constant drops from −1.83k0 to −2.49k0 due to the variation of coupling between array elements. It is concluded that by carefully selecting a combination of radius R, height H, and spacing S we can achieve a desired propagation constant β for a fixed length FCH array. This observation is rather important for the surface wave antenna design, as will be explained in the next section.Figure 8
Parametric study on array geometry parameters: (a) radius; (b) height; (c) spacing.
(a)
(b)
(c)


## 4. Backfire Surface Wave Antenna Design

In this section, a compact 1D, closely spaced parasitic antenna array centered at 400 MHz is designed based on the above identified dominant surface wave mechanism. The total length of the array is assumed to be 0.5λ0. Given this fixed array size, the propagation constant of the surface wave has to be carefully determined to maximize the directivity of the array, which is similar to the 1D metal wire antenna array design [4]. The optimum phase constant βopt for this half-wavelength array is found to be −1.98k0. Then the radius R, height H, and spacing S are selected to be 0.03115 m, 0.049 m, and 0.104 m to achieve this βopt. Other combinations of array geometrical parameters can also result in this optimum propagation constant, as discussed in the previous parametric study. Figure 9 plots the final array design setup, which consists of four FCH elements. The height of the source antenna is tuned to be 0.042 m to match the input impedance to 50 ohms at the center frequency.Figure 9
1D compact, closely spaced backfire antenna array.Figure10 shows the antenna reflection coefficients versus frequency. The center resonance frequencies are found to be 400 MHz and 386 MHz for simulation and measurement. The −10 dB bandwidthes are both 3 MHz. Figure 11 compares the simulated and measured gain in the backward end-fire direction (θ=90°, ϕ=270°). The maximum gain values are 10.99 dBi for simulation and 10.33 dBi for measurement. Finally, Figure 12 plots the simulated antenna array radiation patterns in both the azimuth plane (i.e., xy plane) and the elevation plane (i.e., yz plane) at the center frequency, which clearly shows the backward radiation pattern. The simulated front-to-back ratio is found to be 9.4 dB, while in measurement it is 12.8 dB.Figure 10
Simulated and measured antenna reflection coefficients.Figure 11
Simulated and measured antenna gain.Figure 12
Simulated radiation patterns at 400 MHz: (a) azimuth plane and (b) elevation plane.
(a)
(b)To provide more physical insights into our FCH array operation, we compare its interelement phase delay with the well-known Hansen-Woodyard end-fire array condition [13]. Given the extracted propagation constant (−1.98k0) and spacing (0.138λ0), the phase delay θ0 between adjacent FCH elements is found to be(2)θ0=βoptd=-1.98k0×0.138λ0=-1.72rad.According to the Hansen-Woodyard end-fire array condition, the theoretical optimum phase delay θHW between adjacent array elements should be close to(3)θHW=-k0d+πN=-2πfdc+πN=-1.6525rad,where c is speed of light and N is number of elements. It can be seen thatthe phase delay of our FCH array θ0 is close to that of Hansen-Woodyard end-fire condition θHW, resulting in its maximum radiation in the -y direction.Finally, we compare our FCH antenna array performance with other small antenna arrays in the literatures [14–17]. The comparison is shown in Table 2. It can be clearly seen that our FCH array exhibits the lowest height, highest gain, and best front-to-back (F/B) ratio among all antennas. The tradeoffs we made include one more element and slightly larger spacing. The −10 dB input bandwidth of our antenna is the smallest, which can be attributed to the lowest height of the FCH element.Table 2
Comparison between our antenna and other small antenna arrays in the literatures.
Reference
Number of elements
Spacing
Height
Gain
F/B
BW
Our antenna
4
0.138λ0
0.06λ0
10.3 dBi
12.8 dB
0.75%
[14]
3
0.11λ0
0.275λ0
7.14 dBi
8.6 dB
2.28%
[15]
3
0.06λ0
0.092λ0
8.5 dBi
7 dB
2.7%
[16]
3
0.09λ0
0.1λ0
8.43 dBi
6.63 dB
1.2%
[17]
3
0.053λ0
0.21λ0
9.9 dBi
n/a
12.44%


## 5. Conclusion

In this paper, surface wave propagation and radiation along a 1D FCH array is investigated from both simulation and measurement perspectives. It is found that abackward traveling surface wave can be supported by this structure. The propagation characteristics of this dominant wave mechanism are extracted and discussed. Furthermore, a backfire surface wave antenna is designed and implemented based on the identified wave mechanism. The study presented in this paper opens a new door for low-profile parasitic surface wave antenna array design. For future work, we will expand the study to array structures with other electrically small elements such as the folded spherical helix or the meander line. We will also look into the possibility of applying the FCH antenna array for wireless power transfer.



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*Source: 210254-2015-09-10.xml*