# MIMO Antenna with Isolation Enrichment for 5G Mobile Information

Authors: Nithya S; Seethalakshmi V
Journal: Mobile Information Systems
 (2022)

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## Abstract

A wideband eight-input MIMO array antenna for a fifth-generation smartphone with high enhancement in element segregation is presented. The designed MIMO antenna array comprises eight E-shaped and inverted I-shaped slots on the material with good electrical and thermal conductivity, usually metal. To intensify the bandwidth, the required resonances can be obtained by adjusting the E-shaped slots. Furthermore, to boost the element shielding of the MIMO array antenna system, a single-ended spanner-shaped slot is introduced between each antenna element. As a result, all the elements can cover a wide bandwidth with a frequency range of 3.3 GHz to 6 GHz. The isolation is boosted to 20 dB by a single-ended spanner-shaped slot, and the ECC below 0.04 is measured between any two elements, which show agreeable impedance in far zone radiation characteristics. In the proposed system design, the coupling is induced by the current over a surface on a metallic frame between two antenna components. Consequently, two elements of antenna were separated with an etched slot engraved on a metal frame and used a unique wrench-like resonator to limit the surface current; even though this arrangement increases the free surface of the antenna, it can effectively reinforce the insulation of the element. The performance of the proposed system analyzed certain antenna radiations by handset and head versions. As a consequence, the efficiencies of antennas 2, 3, and 5 are less than 60%, the efficiencies of antenna 8 are around 60%, and the efficiencies of antennas 1, 4, 5, 6, and 7 are even more than 60%. The proposed wideband MIMO antenna device demonstrates reasonably good isolation and low envelope correlation coefficient, both of which are pretty good for fifth-generation MIMO antenna application. The calculated findings show that the planned antenna array’s operating frequency range is capable of covering 3.3 to 6 GHz, with over 20 dB isolation. The antenna will guarantee that the ECC level is smaller than 0.04. The proposed MIMO antenna technology is also efficient for mobile terminal 5G applications.


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## Body

## 1. Introduction

Over the last few years, phenomenal improvement of telecommunication has depleted the potential of existing 4G mobile communication systems. Recently developed communication technology is paying attention to delivering high throughput with minimal time and energy wastage [1]. There is no question that one of the key metrics for potential 5G connectivity would be the data transfer rate. Merchandising of fifth-generation (5G) mobile connectivity, broadband data, and smart mobile networks is nearing [2]. However, there are problems with 5G technology; for example, high-speed demand for the wireless networks MIMO and broadband are needed to address this issue in order to enhance the capacity of the channel and efficiency by exploiting the properties of multipath without changing the power at the input [3]. In comparison with the traditional mobile telephone, 5G mobile phones favour MIMO antenna systems such as 2-, 4-, 8-, 10-, and 12-array antenna systems. Furthermore, the MIMO system should possess the features of broadband and isolation characteristics to lead to a good success. Different nations and operators have set up different frequency bands for 5G communication like the USA with a low and midband of 3700 MHz–4200 MHz and a high band of 64 GHz–71 GHz, Korea with a high band of 26.5 GHz–29.5 GHz, and India with a low and medium band of 3400 MHz–3600 MHz and a high band of 24.5 GHz–29.5 GHz. Broadband is a crucial feature in 5G applications to cover these frequency bands. It is our understanding that the efficiency of the MIMO antenna system will be adversely affected by the mutual coupling of each antenna element. As a result, building a reliable MIMO antenna system to improve element insulation is a challenge. What is more, integrating such a MIMO system into a smart mobile phone with a restricted frame in space is rather difficult [4]. Although the huge 5G antenna is far more competent of enhancing the spectrum efficiency and the data rate, mounting multiple elements in a highly restrictive space in a mobile phone is not an easy task.The proposed compact on-chip antenna is fabricated on a stack of five layers comprising metal silicon. The top silicon layer is sandwiched with two very thin metal layers made of aluminum. The parallel metal layers sandwiching the silicon layer are perforated with a periodic arrangement of circular slot holes, and the two outer edges of the metal layers are connected to each other with metal pins through the silicon layer to create the SIW structure [5]. The top layer consists of a 2 × 4 array of rectangular copper patches. Etched on the patches is a row of subwavelength circular slots. The antenna is excited using proximity coupling at the patch edge, which is analogous to a gap coupling patch. This is achieved with a microstrip coplanar waveguide feedline, which is created by having both sides next to the feedline grounded. The feedline is sandwiched between the two silicon oxide layers, below which is a layer with aluminum patches that are separated from each other by a narrow gap. This layer acts like a partially reflective surface [6]. With the proposed technique, the isolation between the radiating elements was improved on average by 22.5 dB compared to a reference array antenna with no SIW isolation. The performance of the array was enhanced by transforming the patch to exhibit metamaterial characteristics. This was achieved by embedding the patch antennas in the array with subwavelength slots [7]. It is shown that the issues mentioned above afflicting on-chip antennas can be reduced by applying the 2D composite right/left-handed (CRLH) metamaterial transmission line (TL) known as the metasurface concept in the development of the antenna [8]. The performance of the proposed technique, when compared with the conventional on-chip antenna designs, shows improvement in the impedance bandwidth, radiation gain, and efficiency [9].Decoupling technique and the process of making antenna smaller have become an underlying requirement for the design of antenna to satisfy the requirements of a well-packed antenna layout and to increase insulation or isolation. However, more extreme mutual coupling would result in higher antenna elements and lesser distance to one another, thereby degrading the performance of the MIMO antenna system [10]. So, reducing the reciprocal coupling is the main challenge in developing the MIMO array [11, 12]. To fix the issue of separation, several decoupling methods have been implemented. For example, to improve the insulation of the system with a large gap between each antenna element, spatial diversity and polarization diversity were used [13, 14]. To make up the eight-antenna MIMO series, four compact two-antenna construction structures are employed in [15]. Along with the eight elements, the capacity of the channel is greatly improved, but the insulation is only 10 dB. Furthermore, a network of sixteen antennas was studied, which raised the channel bandwidth to 71 bps/Hz [16]. Three neutralization lines guarantee the isolation of 10 dB. A 2 × 2 MIMO monopolistic array with a ground-based decoupling structure has been studied in [17]. This covers the high isolation (more than 20 dB) and low ECCC band of 22–248 GHz (below 0.01). In the meantime, broadband dual antenna structure has been investigated [18], with the use of three neutralization lines to provide segregation which is also adopted in [19]. To reduce mutual coupling in a 2 × 2 MIMO device to a minimum, EBG (electromagnetic bandgap) structure [20, 21] was used, and to reduce mutual coupling, further resonators or hybrid resonators [22–24] were used.This technique is shown to effectively reduce mutual coupling between adjacent radiation elements that can otherwise undermine the arrays radiation gain and pattern. The periphery of each patch is embedded with circular dielectric slots, which are created based on the metasurface concept to enhance the radiation gain and efficiency performances [25]. The advantages of the proposed technique are as follows: (i) simplicity; (ii) cost-effectiveness as there is no need for short-circuited via-holes or three-dimensional metal walls; and (iii) ability to be retrofitted in existing array antennas [26]. An effective method is presented for suppressing mutual coupling between adjacent radiating elements, which is based on metasurface isolation for multiple-input multiple-output (MIMO) and synthetic aperture radar (SAR) systems. This is achieved by choking surface current waves induced over the patch antenna by inserting a cross-shaped metasurface structure between the radiating elements [27]. Two patch antennas are electromagnetically coupled through the substrate media and space above and below it. Coupling on the substrate layer is due to surface waves, and the coupling through the air is through direct patch-to-patch near field [28]. One of the two couplings is more dominant, which depends on the spatial geometry of the antenna structure. Direct mutual coupling between the patch elements can be controlled by adding an extra indirect coupling path using the proposed EBG-MTM isolation structure [29]. Multiple-input multiple-output (MIMO) systems enable high-capacity wireless communications without increasing the signal bandwidth or signal-to-noise ratio (SNR). This is because the multiple data streams can be transmitted simultaneously by using multiple antennas (antenna array) at the transmitter and receiver [30]. To realize compact MIMO antennas, the critical challenge is to minimize the signal correlation between antennas over a wide frequency range. When multiple antennas are placed close, the mutual coupling can degrade the radiation performances of the antennas and the channel capacity of MIMO systems [31].In [17], between the antenna elements, an inverted I ground slot with enhanced element segregation of 20 dB has been introduced. A multimode decoupling element similar to a tree has been registered in [32], and broadband isolation has been carried out, but it is still bulky and has no easy adjustment features; in principle, due to the extremely complicated electromagnetic (EM) setting, a multimode resonator of miniaturized size (decoupling element) is difficult to regulate. The majority of decoupling networks are of filter type [11, 33–35]. Hence, it is possible to realize multidecoupling modes by referring to the multimode filter theory of architecture. To achieve pattern diversity, the methodology outlined in [36] uses a ring slot, which ensures isolation in excess of 15 dB between the ports of larger size (80 × 80 mm2). To boost the separation, a variety of decoupling structures or various stubs were employed between any two radiators. To achieve pattern and polarization diversity, feeding directions with perpendicular arrangement were employed in [37–40]. In this paper, isolation enrichment with an eight-input MIMO array antenna for a fifth-generation smart mobile system is presented. E-shaped and inverted I-shaped slots were carved on the metal frame for exploring new radiation methods in the design of MIMO smart mobile phone antenna space-restricted, in contrast to other models, affected by the limited radiation-induced environment of the metal structure. To improve the insulation of the components of the MIMO array antenna system, a one-end wrench slot was suggested. Consequently, the wide spectrum of the MIMO array antenna system is obtained, and the isolation of the element is around 20, which can cover a larger part of the range of less than 6 GHz. As in Table 1, the suggested fifth-generation MIMO array antenna system outperforms the state of technology in this area.Table 1
Comparative rendering with previously published literature.
ReferenceAntenna element sizeDecoupling methodIsolationECCEffective bandwidth (GHz)Total efficiency (%)ComplexityProposed150 × 80 × 7 mm3 (eight elements)Ground slot20<0.043.3 GHz–5.82 GHz50–92Simple[4]150 × 75 × 7 mm3 (eight elements)Ground slot>18<0.053.3 GHz–6.0 GHz40–90Complex[12]17.4 × 6 × 0.8 mm3 (single element)No>19.6<0.0133.0 GHz–6.0 GHz49–76.9Complex[17]124 × 74 × 6 mm3 (eight elements)Hybrid method (neutralization line and ground slot)>15<0.153.3 GHz–3.6 GHz40–60Simple[20]150 × 80 × 0.8 mm3 (eight elements)Ground slot>11<0.153.4 GHz–3.8 GHz5.15 GHz–5.9 GHz45–65Simple[22]150 × 75 × 0.8 mm3 (eight elements)Neutralization line10<0.323.3 GHz–3.6 GHz40–52Simple[23]150 × 80 × 0.8 mm3 (eight elements)No>17.5<0.053.3 GHz–3.6 GHz62–76Simple[32]150 × 75 × 8 mm3 (eight elements)Polarization orthogonal>17<0.13.4 GHz–3.6 GHz49–72Moderate[34]145 × 75 × 6 mm3 (eight elements)No>15<0.163.4 GHz–3.6 GHz42–73Complex[7]150 × 75 × 6.8 mm3 (eight elements)No>14.7<0.053.3 GHz–5.0 GHz46–80Complex[9]36 × 36 × 1.9 mm3 (four elements)Pattern diversity>10.8<0.083.4 GHz–3.6 GHz62–80Complex[25]160 × 68 × 0.8 mm3 (eight elements)Pattern diversity15<0.153.3 GHz–5.0 GHz68–82Medium


## 2. Design of MIMO Antenna

Multiple-input-multiple-output (MIMO) antennas with the ability to radiate waves in more than one pattern and polarization play a great role in modern telecommunication systems. This paper provides a theoretical review of different mutual coupling reduction techniques in MIMO antenna systems. The increase in the mutual coupling can affect the antenna characteristics drastically, thus degrading the performance of the MIMO systems. It is possible to improve the performance partially by calibrating the mutual coupling in the digital domain. A millimeter-wave (MMW) antenna is presented for the fifth-generation (5G) wireless multiple-input multiple-output (MIMO) applications in order to offer numerous advantages, including compactness, planar geometry, high bandwidth, and high gain performance. The concept of defected ground structures has been deployed for the first time in MIMO antenna design at the MMW spectrum to fulfil 5G requirements of high bandwidth with compactness and low design complexity. The top surface of the antenna comprises a coplanar waveguide-fed T-shaped radiating patch element, while the bottom part is designed to constitute a partial ground loaded with two iterations of symmetrical split-ring slots at an optimized distance. The general view of the 5G MIMO antenna device designed to fit the 5G smart mobile phone framework is shown in Figure1(a).Figure 1
(a) General view of 5G MIMO antenna. (b) 5G MIMO antenna with feed line and decoupling element. (c) Dimensions of 5G MIMO antenna with feed line and decoupling element.
(a)(b)(c)The field scale is 150 × 80 mm2, and the handset is with a thickness of 7 mm. To create the body of the smartphone, an FR4 substrate with a thickness of 0.8 mm, relative permittivity of 4.4, and tangent loss of 0.02 is used. For the manufacture of the frame and the circuit board, whose relative permittivity is 4.4 and the loss tangent is 0.02, the 0.8 mm thick FR4 substrate is used, and copper for the radiation element (conductivity 5.8 × 107 S/m) is used. Copper conductivity is very robust, and it has no effect on the matching of impedance. The size of the antenna substrate is 150 × 80 × 7 mm3, which is compatible with a mobile phone.The structure of slot antenna 1 (Ant 1) and antenna 2 (Ant 2) is illustrated in Figures1(b) and 1(c). The 8-slot antenna part arrangement is as follows. The 1, 3, 5, and 7 and 2, 4, 6, and 8 antennas are arranged vertically along the two sides of the PCB (right and left). Every antenna part can completely cover the 3.3 GHz to 5 GHz band in this design. As can be seen, the 14 mm × 27 mm E-shaped slot is first engraved on the surface of the ground, which serves as the main radiator of the multiband antenna. The inverted “I” shape is formed by slicing a 16 mm × 5.5 mm opening section over an E-shaped slot. The E-shaped slot that is couple-fed by an inverted L-shaped feed strip is merely 11.8 mm displaying that the antenna function offered has an adequate size for a smart mobile phone.The feeding strip consists of 2 parts, namely, the 11.8 mm × 1.5 mm vertical segment (50 ohm microstrip feed line) and a small horizontal adjustment section or an adjustment tip stretching from a point, with a dimension of lengthL (mm) × width W mm. The slot antenna element suggested is well energized and balanced by regulating the length L, width W, and the relative position of the adjusting section. The simulation tool is able to accomplish these slot parameters (L1, L2, and L3) and the separation distance between them. To achieve maximum efficiency of the suggested MIMO antenna array, two dissimilar mechanisms were implemented. The slot parameter of the antenna L1 (mm), L2 (mm), and L3 (mm) was varied from each antenna element, as shown in Table 2. The antenna element is a kind of open slot, and four resonance modes are energized by means of E-shaped slots that are dependent heavily on its nearby terrain. To attain a stronger performance agreement, antenna elements are arranged differently with different dimensions, which are reformed and defined effectively.Table 2
Variations ofL1,L2, and L3 of E slot element.
L1 (mm)L2 (mm)L3 (mm)214.52.523.532.42.83.522.5422.0A simpler and faster method than the one previously described derives the correlation coefficient from the S parameters of the antennas, that is, the port reflection coefficients S11 and S22 of the two antennas, and the coupling S21 = S12. Several publications present the relation between the S parameters and the correlation coefficient.Total radiated powers for the two antennas are(1)Prad,1=1−S112−S212η1,Prad,2=1−S222−S122η2,from which the definition of radiation efficiencies η1 and η2 is clear. Internal losses for the two antennas are from this concluded to be given by(2)Ploss,1=1−S112−S2121−η1,Ploss,2=1−S222−S1221−η2,0=S11S12∗+S21S22∗1−S112−S2121−S222−S122+ρrecη1η2+ρloss1−η11−η2.Since the expression on the right-hand side in the above equation is zero, one unknown term can be calculated if the other terms are known. The principle of the method of calculating received signal correlation from S parameters is to measure the first term and take the second term to be the negative of this value.S21: the measured S parameter is 26 dB at 3.5 GHz, 22 dB at 4.5 GHz, and 20 dB at 5.5 GHz.S32: the measured S parameter is 23 dB at 3.5 GHz, 32 dB at 4.5 GHz, and 47 dB at 5.5 GHz.S31: the measured S parameter is 25 dB at 3.5 GHz, 21 dB at 4.5 GHz, and 20 dB at 5.5 GHz.S51: the measured S parameter is 26 dB at 3.5 GHz, 30 dB at 4.5 GHz, and 32 dB at 5.5 GHz.To examine the resonant mechanisms, create slots by regulating the electrical length of E and I. However, the antenna with E and I slots resonates at 4 different frequenciesFigures2(a) and 2(b) show that the 1st resonance spreads predominantly around the E-shaped slots. The 2nd and 3rd resonance surface currents are primarily concentrated in the slot of “I shape.” However, the 4th resonance originates from the mating between the E- and I-shaped slots. By changing the electrical length of unaltered I-shaped slots, we studied the resonant mechanisms. It is found that the resonance changes to high frequency in the 1st, 2nd, 3rd, and 4th, while the 3rd resonance remains unchanged. In contrast, the length of I-shaped slots is increased, and the length of E-shaped slots is kept unaltered. The 2nd, 3rd, and 4th resonances explicitly shift to a lower frequency, while the 1st resonance stays unchanged. We can infer that the first resonance comes from the E-shaped slot, the second and third resonance can come from I-shaped slots, the fourth resonance is born from the E- and I-shaped slots coupling. Finally, a frequency range from 3.3 GHz to 6 GHz can support the proposed antenna feature, with a reflection coefficient lesser than the standing wave ratio of −6 dB (3 : 1) voltage.Figure 2
(a) Antenna element input impedance. (b) Antenna element input impedance with the variation of E-shaped slot.
(a)(b)


## 3. Decoupling Element

The main idea of the decoupling algorithm proposed by Boksenbom and Hood is making the overall closed-loop transfer function of the controlled MIMO system diagonal. So far, this is still the primary solution to the coupling problem. Some other remarkable contributions have been made based on this idea. For single-input-single-output (SISO) systems, there is a widely accepted time delay compensation algorithm named Smith Predictor. This compensation algorithm was improved to be applicable to MIMO systems with multivariable delays by Ogunnaike and Ray under some specified assumptions. Other developments aiming at multivariable Smith Predictor can be found. These decoupling methods are mainly focused on systems with multivariable delays. These decoupling methods tried to make the MIMO system decoupled first, so the interactive MIMO system control problem would be transformed into multiple single loops system control problems. Then, the Smith Predictor can be designed based on the decoupled system. However, the uncertain accuracy of the predictor, unrealizable matrix inversion expression, and complicated decoupling procedure have kept Smith Predictor decoupling away from being extensively applied in industrial processes.Here, a variety of decoupling techniques were initiated to improve the separation between each of the two antenna components. In our design, the coupling is induced by the current over a surface on a metallic frame between two antenna components. Consequently, two elements of antenna were separated with an etched slot engraved on a metal frame and used a unique wrench-like resonator to limit the surface current; even though this arrangement increases the free surface of the antenna, it can effectively reinforce the insulation of the element.For the MIMO array antenna system, this approach is recommended with a larger requirement of isolation but low clearing restriction. Our decoupling-free design can also satisfy the demand for the requirement of the antenna with very restricted clearance but with less segregation requirement. In order to check the element decoupling mechanism, the distribution of surface current in the absence and presence of decoupling structure is shown in Figures3(a) and 3(b). A comparison of the distribution of the surface current between Figures 3(a) and 3(b) shows that when the first antenna is energized and excited, the second antenna is terminated with 50 Ω load, and the decoupling factor proposed here successfully precludes the surface current flowing from antenna 1 to antenna 2. Then, in the situation of with and without decoupling components, the transmission coefficients between two pairs of antenna 1, antenna 2, and antenna 3 were shown in Figures 4 and 5. Clearly, with the decoupling structure, the degree of element insulation is enhanced to more than 20 dB, which is highly competitive in this regard.Figure 3
(a) Absence of decoupling structure between antennas 1 and 2. (b) Presence of decoupling structure between antennas 1 and 2.
(a)(b)Figure 4
Transmission coefficient without decoupling structure.Figure 5
Transmission coefficient with decoupling structure.


## 4. Results and Discussion

### 4.1. S Parameters

The transmission coefficient, reflection coefficient, and S parameters of antenna design are discussed in the following. The MIMO antenna design which is proposed here can support a broadband range from 3.3 GHz to 6.0 GHz with a reflection coefficient less than −6 dB (3 : 1 VSWR).


### 4.2. Transmission Coefficient

Transmission coefficient between any antenna pairs 1, 2, and 3 in the case of a decoupling element with or without the decoupling element is shown in Figures4 and 6. It clearly shows that, without decoupling structure, the element isolation is around −15 dB; obviously, the insulation of the elements is enhanced by more than −20 dB with the aid of decoupling structure. The reflection coefficient between the ports S21, S32, S51, and S62 was analyzed because ports 1 and 2, 2 and 3, 1 and 5, and 2 and 6 are adjoining to one another and as well the coupling among them is more powerful than the other pair. The simulated values fit well, and the isolation of the element exceeds −20 dB in the target frequency band.Figure 6
Simulated reflection coefficients.Simulated results of antenna efficiency are shown in the following; Figure7 clearly shows that the effectiveness of the antenna is greater than 80% on all target frequency bands.Figure 7
Simulated result of antenna efficiency.The envelope correlation coefficient (ECC) of the system proposed in this section was analyzed. ECC is an important consideration in accessing the multiplexing and the diversity of the MIMO antenna system. Figure8 represents the virtual ECC of antenna pairs 1 and 2, 2 and 3, 1 and 5, and 2 and 6. The pairs of antennas are preferred, as they are close to one another. For simplicity’s sake, the envelope correlation coefficient of the pair of antennas, which is in a symmetrical manner, is not included here. In the above figure, ECC in the targeted frequency range is lower than 0.04, offering a promising output.Figure 8
Simulated envelope correlation coefficient result (ECC).


### 4.3. Performance Metrics on Radiation Pattern

In this section, the radiation pattern of antenna 1 and the radiation pattern of antenna 2 were analyzed. Instead of the symmetrical MIMO layout, the radiation models of other antenna components of the antenna system are not included for simplicity here. The simulated 3D radiation patterns of antenna 1 operated at three different frequencies like 3.5 GHz, 4.5 GHz, and 5.5 GHz are represented in Figure9(a) and 3D radiation patterns of antenna 2 operated at three different frequencies like 3.5 GHz, 4.5 GHz, and 5.5 GHz are represented in Figure 9(b), respectively. Figures 9(a) and 9(b) show that antenna 1’s maximal radiation path is inclined and indicating the third quadrant or clock face is at 3.5 GHz; antenna 1 antenna patterns are skewed at 4.5 GHz and 5.5 GHz, too. The justification is that, for antenna 1, the field is asymmetrical. And in Figure 9(b), antenna 2’s radiation variations appear more symmetric around the frequency range than those of antenna 1. In fact, the ground of antenna 2 is relatively symmetrical in relation to the ground of antenna 1. Consequently, the overall radiation paths of antenna 1 and antenna 2 do not point through the frequency band to each other, resulting in a respectable ECC of less than 0.04.Figure 9
(a) 3D radiation pattern for antenna 1 simulated at 3.5 GHz, 4.5 GHz, and 5.5 GHz. (b) 3D radiation pattern for antenna 2 simulated at 3.5 GHz, 4.5 GHz, and 5.5 GHz.
(a)(b)


### 4.4. Performances of MIMO Antenna

## 4.1. S Parameters

The transmission coefficient, reflection coefficient, and S parameters of antenna design are discussed in the following. The MIMO antenna design which is proposed here can support a broadband range from 3.3 GHz to 6.0 GHz with a reflection coefficient less than −6 dB (3 : 1 VSWR).


## 4.2. Transmission Coefficient

Transmission coefficient between any antenna pairs 1, 2, and 3 in the case of a decoupling element with or without the decoupling element is shown in Figures4 and 6. It clearly shows that, without decoupling structure, the element isolation is around −15 dB; obviously, the insulation of the elements is enhanced by more than −20 dB with the aid of decoupling structure. The reflection coefficient between the ports S21, S32, S51, and S62 was analyzed because ports 1 and 2, 2 and 3, 1 and 5, and 2 and 6 are adjoining to one another and as well the coupling among them is more powerful than the other pair. The simulated values fit well, and the isolation of the element exceeds −20 dB in the target frequency band.Figure 6
Simulated reflection coefficients.Simulated results of antenna efficiency are shown in the following; Figure7 clearly shows that the effectiveness of the antenna is greater than 80% on all target frequency bands.Figure 7
Simulated result of antenna efficiency.The envelope correlation coefficient (ECC) of the system proposed in this section was analyzed. ECC is an important consideration in accessing the multiplexing and the diversity of the MIMO antenna system. Figure8 represents the virtual ECC of antenna pairs 1 and 2, 2 and 3, 1 and 5, and 2 and 6. The pairs of antennas are preferred, as they are close to one another. For simplicity’s sake, the envelope correlation coefficient of the pair of antennas, which is in a symmetrical manner, is not included here. In the above figure, ECC in the targeted frequency range is lower than 0.04, offering a promising output.Figure 8
Simulated envelope correlation coefficient result (ECC).


## 4.3. Performance Metrics on Radiation Pattern

In this section, the radiation pattern of antenna 1 and the radiation pattern of antenna 2 were analyzed. Instead of the symmetrical MIMO layout, the radiation models of other antenna components of the antenna system are not included for simplicity here. The simulated 3D radiation patterns of antenna 1 operated at three different frequencies like 3.5 GHz, 4.5 GHz, and 5.5 GHz are represented in Figure9(a) and 3D radiation patterns of antenna 2 operated at three different frequencies like 3.5 GHz, 4.5 GHz, and 5.5 GHz are represented in Figure 9(b), respectively. Figures 9(a) and 9(b) show that antenna 1’s maximal radiation path is inclined and indicating the third quadrant or clock face is at 3.5 GHz; antenna 1 antenna patterns are skewed at 4.5 GHz and 5.5 GHz, too. The justification is that, for antenna 1, the field is asymmetrical. And in Figure 9(b), antenna 2’s radiation variations appear more symmetric around the frequency range than those of antenna 1. In fact, the ground of antenna 2 is relatively symmetrical in relation to the ground of antenna 1. Consequently, the overall radiation paths of antenna 1 and antenna 2 do not point through the frequency band to each other, resulting in a respectable ECC of less than 0.04.Figure 9
(a) 3D radiation pattern for antenna 1 simulated at 3.5 GHz, 4.5 GHz, and 5.5 GHz. (b) 3D radiation pattern for antenna 2 simulated at 3.5 GHz, 4.5 GHz, and 5.5 GHz.
(a)(b)


## 4.4. Performances of MIMO Antenna

## 5. Impacts on Operators Hand and Head Style

Finally, Section 5 shows the influence of the one-hand model, double-hand model, and operator’s head-hand model. In multiple cases, the propagation coefficient, variance of reflection coefficients, and radiation efficiencies were investigated, respectively. In Figure10 along with its subsections (a, b, c, and d), the one-hand model simulates the MIMO antenna system. Although the adequacy of the impedance to the lower frequency band has deteriorated slightly, all antennas are still able to cover 3.3–6.0 GHz.Figure 10
(a) One-hand model. (b) One-hand model’s transmission coefficient. (c) One-hand model’s reflection coefficient. (d) One-hand model’s antenna efficiency.
(a)(b)(c)(d)The isolation of the components remains over 20 dB. Their radiation efficiencies decreased dramatically due to antennas 1-2’s direct finger touch, although the efficiencies of antennas 3 to 8 remain higher than 60% in the target frequency range. In Figure11 along with its subsections (a, b, c, and d), with a dual-hand model, the MIMO array antenna system is simulated. Thumbs are influenced by antennas 5 and 8, resulting in the balancing of degenerate impedance and radiation quality. Nevertheless, the isolation of the element is over 20 dB and performance is above 60 percent; antennas 1, 2, 3, 4, 6, and 7 and 8 still operate at 3.3–6.0 GHz. In Figure 12 along with its subsections (a, b, c, and d), a head-hand model simulates the MIMO antenna system. The coefficients of reflection remain constant, and the isolation of the element remains 20 decibels. In comparison, certain antennas’ radiation efficiencies were reduced because a portion of radiated energy was consumed by the hand and head versions. As a consequence, the efficiencies of antennas 2, 3, and 5 are less than 60%, the efficiencies of antenna 8 are around 60%, and the efficiencies of antennas 1, 4, 5, 6, and 7 are even more than 60%. The proposed wideband MIMO antenna device demonstrates reasonably good isolation and low envelope correlation coefficient, both of which are pretty good for the fifth-generation MIMO antenna application. The calculated findings show that the planned antenna array’s operating frequency range is capable of covering 3.3 to 6 GHz, with over 20 dB isolation. The antenna will guarantee that the ECC level is smaller than 0.04. The proposed MIMO antenna technology is also efficient for mobile terminal 5G applications. In the future, research will be improved further by including various multioutput signal parameters with antenna efficiency.Figure 11
(a) Double-hand model. (b) Transmission coefficient of double-hand model. (c) Reflection coefficient of double-hand model. (d) Antenna efficiency of double-hand model.
(a)(b)(c)(d)Figure 12
(a) Head-hand model. (b) Transmission coefficient of head-hand model. (c) Reflection coefficient of head-hand model. (d) Antenna efficiency of head-hand model.
(a)(b)(c)(d)


## 6. Conclusion

In this work, for 5G mobile applications, an eight-part MIMO array antenna system is planned. The fifth-generation MIMO array antenna can operate properly using a portion of the metal frame. It was verified by simulation that it is possible to achieve the suggested antenna with effective antenna isolation using the decoupling technique. In specific, the proposed wideband MIMO antenna device demonstrates reasonably good isolation and low envelope correlation coefficient, both of which are pretty good for fifth-generation MIMO antenna application. The calculated findings show that the planned antenna array’s operating frequency range is capable of covering 3.3 to 6 GHz, with over 20 dB isolation. The antenna will guarantee that the ECC level is smaller than 0.04. The proposed MIMO antenna technology is also efficient for mobile terminal 5G applications.



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*Source: 1802352-2022-02-21.xml*