# A Wideband Dual-Polarized Antenna Using Planar Quasi-Open-Sleeve Dipoles for Base Station Applications

Authors: Guan-xi Zhang; Li Sun; Bao-hua Sun
Journal: International Journal of Antennas and Propagation
 (2015)

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## Abstract

A wideband dual-polarized antenna for WLAN, WiMAX, and LTE base station applications is presented in this paper. The proposed antenna consists of two pairs of orthogonal planar quasi-open-sleeve dipoles along the centerlines, a balanced feeding structure and a square ground plane. The planar quasi-open-sleeve dipole comprises a pair of bowtie-shaped planar dipoles with two parallel curve parasitic elements. The introduced parallel curve parasitic elements change the path of the current of the original bowtie-shaped planar dipoles at high frequencies and hence wideband characteristic is achieved. Two pairs of the planar quasi-open-sleeve dipoles placed orthogonally further broaden the bandwidth of the antenna with dual-polarization characteristics. The proposed antenna achieves a 10-dB return loss bandwidth from 2.32 to 4.03 GHz (53.9% bandwidth) using the planar quasi-open-sleeve dipole structures. The isolation between the two ports remains more than 32 dB in the whole bandwidth. Measured results show that the proposed antenna keeps the cross-polarization under −33 dB and the front-to-back ratio better than 15 dB in the operating band. The antenna has an area of 0.3λ  × 0.3λ at 2.32 GHz making it easy to be extended to an array element.


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## Body

## 1. Introduction

Dual-polarized antennas have obtained wide applications in various mobile communications such as WLAN, WiMAX, and LTE base stations. In order to cover these bands, dual-polarized antennas are required to have a broad bandwidth. In addition, high port-to-port isolation and low cross-polarization level are also required for base station antennas. Designing the dual-polarized antennas that meet these requirements is a challenging work.Several techniques have been developed to improve the bandwidth [1–4]. A feeding structure of aperture coupling has applied in [1–3] achieving an impendence bandwidth about 20%. The feeding structure can also improve the port isolation. A stacked patch is introduced that obtains an impedance bandwidth over 33% in [4]. However, all these antennas have the disadvantages of high cross-polarization levels due to the transverse currents of high-order modes.Several techniques have been developed to improve the port isolation and the cross-polarization [5–10]. The antennas in [5–7] are symmetrically excited by a differential feed system with a phase difference of 180°. This feeding structure can improve the cross-polarization by suppressing the higher-order modes. A balanced feeding structure with two shorting pins and two feeding coax lines is introduced in [8–10] to improve the isolation. The antenna in [10] also achieves a wide impendence bandwidth of 45.8%.The cylindrical open-sleeve dipole contains a dipole with two closely spaced parasitic elements or sleeves [11]. This kind of antennas takes the merits of broadband characteristic [12]. In recent decades, the planar open-sleeve dipole has been investigated in many literatures [13–15]. These antennas are conformal and can be used to achieve a broadband/dual-band characteristic. The end-loaded planar open-sleeve dipole antenna in [13] achieves a wide impendence bandwidth of 50%. Unfortunately, these antennas are single linear polarization. The planar open-sleeve dipole has not been used as dual-polarized antennas.In this paper, a wideband dual-polarized antenna with planar quasi-open-sleeve dipole structures is presented. A pair of bowtie-shaped planar dipoles and two parallel curve parasitic elements constitute the planar quasi-open-sleeve dipole structures with wideband characteristics. Better wideband and dual-polarization characteristics are achieved by orthogonally placing two pairs of planar quasi-open-sleeve dipoles. The proposed antenna achieves a 10-dB return loss bandwidth from 2.32 to 4.03 GHz (53.9% bandwidth) using the planar quasi-open-sleeve dipole structures. By introducing two feeding coax lines with two shorting pins as the balanced feeding structure, the isolation between the two ports remains more than 32 dB in the operating band. Experimental results of the constructed prototype show good cross-polarization performance. Details of the antenna design and both theoretical and experimental results are presented and discussed in the following sections.


## 2. Antenna Geometry

The geometry of the proposed dual-port and dual-polarized wideband planar dipole is given in Figure1, with detailed dimensions shown in Table 1. The antenna was constructed by printing it on RF4 substrate, with a thickness of 1 mm, a relative permittivity of 4.4, and an area of 40 mm × 40 mm. In the design, the bowtie-shaped planar dipoles unite the curve parasitic elements, printed to the surface of the structure. A balanced feeding structure, shown in Figure 1, consists of two shorting pins and two feeding coax cables. The two coax lines are placed along the centerline of the radiating patch and are located at a distance of S/2 from the center of the patch. The outer part of the feeding coax cable is connected to one arm of the dipole (yellow circle in Figure 1) and the inner part connected to the other arm of the dipole (red circle in Figure 1). With two shorting pins connecting to the inner part of the feeding coax, good isolation between the two ports is achieved.Table 1
Dimensions of the proposed antenna.
Parameters
G
H
P
L
L
1
L
2
L
3
Values/mm
100
27.4
40
9
4.9
17.2
Parameters
W
0
W
1
W
2
S
D
0
D
1
Values/mm
1
4
8
5
2
2.4
Parameters
α
Values/degree
53Figure 1
Geometry of the proposed antenna with the detailed design parameters.


## 3. Principle of Operation

To better understand the excitation behavior of the proposed antenna, Figure2 shows the evolution steps of the proposed antenna design. Antenna A is shown in Figure 2(a), which is composed of a class planar bowtie-shaped dipole operating at 2.5 GHz. In order to verify the impact of two curve parasitic elements on the planar bowtie-shaped dipole antenna, two curve parasitic elements perpendicular to the axis of the bowtie-shaped dipole are added symmetrically to both sides of the antenna, as shown in Figure 2(b). In order to widen the bandwidth of the bowtie-shaped dipole, two curve parasitic elements parallel to the axis of the bowtie-shaped dipole are added symmetrically to both sides of the antenna. Antenna C shown in Figure 2(c) is designed. Finally, for obtaining double linear polarizations, two pairs of planar quasi-open-sleeve dipoles which are perpendicular are printed on the substrate, as the proposed antenna (Antenna D) presented in Figure 2(d).Figure 2
The evolution steps of the proposed antenna configuration: (a) a planar bowtie-shaped dipole (Antenna A), (b) a planar bowtie-shaped dipole with two curve parasitic elements (Antenna B), (c) a planar bowtie-shaped dipole with four curve parasitic elements (Antenna C), and (d) the proposed antenna (Antenna D).Figure3 illustrates the S
11 variation of Antenna A, Antenna B, Antenna C, and Antenna D. It can be seen that Antenna A shows good impedance matching at 2.5 GHz. By adding two perpendicular curve parasitic elements, the resonance frequency shifts slightly from 2.5 GHz to 2.4 GHz. It is noticed that the perpendicular curve parasitic element does not destroy the resonance characteristic of Antenna A. By adding another two parallel curve parasitic elements on Antenna B, a new upper resonant frequency around 4 GHz is generated without changing the resonance characteristics at 2.4 GHz. Antenna C shows broadband characteristics with lower resonant frequency at 2.4 GHz weakened. Finally, by placing two pairs of planar quasi-open-sleeve dipoles perpendicularly, the proposed antenna (Antenna D) achieves good advantage of broadband characteristics with both lower and upper resonant frequencies enhanced.Figure 3
Simulated|
S
11
| performances of the antennas.To further validate the wideband characteristics, the current distributions of the proposed dual-polarized antenna at 2.5 GHz and 3.6 GHz are depicted in Figure4 when Port 2 is excited. It is obvious that the current mainly flows along the horizontal bowtie-shaped dipole at 2.5 GHz. The bowtie shaped structure diminished the dimension of the antenna while the introduced curve parasitic elements have little influence on the current distributions at 2.5 GHz. Thus, the operation for lower band is achieved by the horizontal bowtie-shaped dipole. As shown in Figure 4(b), the introduced curve parasitic elements change the patch of the current with the currents mainly flowing along the four curve elements instead of the bowtie-shaped dipole at 3.6 GHz. Furthermore, the currents on the two horizontal curve parasitic elements are in phase, while the currents on the two vertical curve parasitic elements are out of phase. Thus, the current along the y-axis is enhanced while the current along x-axis is offset. Therefore, the proposed antenna achieved resonating at 3.6 GHz with the same polarization as the lower resonance frequency.Figure 4
Current distribution of the proposed antenna at (a) 2.5 GHz and (b) 3.6 GHz for Port 2.
(a)
(b)


## 4. Simulated and Measured Results

The proposed antenna is designed, constructed, and tested. Figure5 shows the photograph of the proposed antenna. The simulated and measured reflection coefficients of each port of the proposed antenna are shown in Figure 6. It can be seen that the antenna exhibits a measured −10 dB impedance bandwidth of 1730 MHz and 1740 MHz for Port 1 and Port 2, respectively, which can cover WLAN (2400–2484 MHz), LTE (2500–2690 MHz), and WiMAX (3300–3800 MHz). The measured S11/S22 characteristics shown in Figure 6 imply that the mutual coupling of parasitic elements is greater than expected from the simulations. Besides, the asymmetry of S11 and S22 results from the coupling effects in feeding structure. The simulated and measured S21 between the two ports are shown in Figure 7. It is observed that the simulated port isolation and measured port isolation are better than 33 dB over the frequency band from 2.32 GHz to 4.03 GHz. The deterioration of isolation in higher frequencies is caused by the effect of parasitic elements and its mutual coupling shown in Figure 4.Figure 5
Photograph of the proposed antenna.Figure 6
Measured and simulated S11/S22 of the proposed antenna.Figure 7
Measured and simulated S21 of the proposed antenna.Measured radiation patterns in both of E- and H-plane at 2.5 GHz, 3 GHz, and 3.5 GHz for Port 1 are illustrated in Figures8 and 9, respectively. Owing to the symmetrical characteristic of the proposed antenna, the radiation patterns of the proposed antenna have only a slight difference between the two ports. Thus, we just show the measured radiation results of Port 1. When one port is measured, the other port is connected to the matched load.Figure 8
Measured radiation patterns for E-plane (xoz plane) at (a) 2.5 GHz, (b) 3 GHz, and (c) 3.5 GHz for Port 1.
(a)
(b)
(c)Figure 9
Measured radiation patterns for H-plane (yoz plane) at (a) 2.5 GHz, (b) 3 GHz, and (c) 3.5 GHz for Port 1.
(a)
(b)
(c)It can be seen that the measured cross-polarization levels within the main lobe are less than −32 dB in both E- and H-plane for the two ports, while the front-to-back ratio remains over 15 dB due to small metallized ground plane. The simulated and measured gains of the antenna are shown in Figure10. The gain for the two ports ranges from 7.2 dBi to 7.8 dBi within the operation frequency band.Figure 10
Measured and simulated gain of the proposed antenna.


## 5. Conclusion

In this paper, a wideband dual-polarized antenna with low cross-polarization and high isolation is designed by using two pairs of orthogonal planar quasi-open-sleeve dipoles. The introduced curve parasitic elements change the path of the current distributions at higher resonant frequencies but achieve the consistent polarization in the whole operating band. The proposed antenna is excited by two feeding coax lines and shorted by two pins as the balancing feeding structure. A prototype with center frequency of 3.1 GHz was designed, fabricated, and tested. The proposed antenna achieves a 53.9% impedance bandwidth for 10-dB return loss (2.32 GHz–4.03 GHz), a −32 dB cross-polarization level for both polarization with low back radiation, a 33 dB port isolation, and an average gain of 7.5 dBi in the whole bandwidth. Work is in progress to realize a 2 × 2 planar array to be used as a small cell antenna for mobile communication base stations.



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*Source: 164392-2015-08-12.xml*