# Two-Step Beveled UWB Printed Monopole Antenna with Band Notch

Authors: Yan Xiao; Zhong-Yong Wang; Ji Li; Zi-Lun Yuan; A. K. Qin
Journal: International Journal of Antennas and Propagation
 (2014)

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## Abstract

This paper presents a novel compact printed monopole ultra-wideband (UWB) antenna featured with the band notch. The proposed antenna consists of a two-step beveled radiant patch and a truncated ground plane, which can provide a good impedance matching from 3.1 GHz to 10.6 GHz. In order to generate the band-notched characteristics, two symmetrical slots are embedded along with the microstrip feeding line, resulting in a band notch from 5.05 GHz to 5.85 GHz. Accordingly, the mutual electromagnetic interference between the UWB and wireless local area network (WLAN) radio communication systems can be eliminated. In addition, it is shown how the slots integrated on the ground plane improve the radiation patterns. The experimental measurements are found to be in good agreement with the numerical simulations.


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## Body

## 1. Introduction

In 2002, the Federal Communications Commission (FCC) approved the use of the unlicensed band with the frequencies ranging from 3.1 GHz to 10.6 GHz in the commercial ultra-wideband (UWB) wireless communication systems [1]. This invoked a surge in research on the UWB communication technology. Impulse radio UWB (IR-UWB) is a promising UWB communication technique having a simple architecture. In the IR-UWB systems, short duration pulses are usually adopted as exciting signals. However, as a well-known fact, the presence of frequency distortions in the surface current distribution excited on the antenna will give rise to strongly distorted radiated signals. Therefore, to enable the antenna to radiate undistorted pulses, the design of antennas in the UWB systems is subject to the following requirements. Firstly, the impedance band must cover the frequency range from 3.1 GHz to 10.6 GHz. Secondly, the radiation patterns must be uniform over the entire operational band. Recently, the UWB antenna design has received more and more attention.Thanks to their inherent advantages (e.g., the low cost, the easy integrability with the passive and active components, etc.), various types of printed antennas, such as the printed dipoles [2–4] and the printed monopoles, and the slot antennas [5, 6] have been widely used in the UWB communication systems.Cappelletti et al. developed an antipodal drop-shaped dipole antenna [2]. This antenna not only can exhibit the good radiation performance in the frequency domain but also demonstrate the excellent signal fidelity in the time domain. It is fabricated on a thin flexible substrate, which can be made conformal easily. Moreover, the authors described a method useful to realize a compact array of antennas. Quintero and Skrivervik produced a dipole antenna that is symmetrical and elliptical [3]. This antenna is differential and can be directly connected to a differential circuit. Teni et al. fabricated an antipodal Vivaldi antenna [4] that operates over a broad frequency range from 5 GHz to 30 GHz. This antenna has the peak gain over 5 dBi and presents stable radiation patterns. As an important class of planar radiators, such dipole antennas have several unique advantages. Firstly, they can reduce the level of the field radiated in the direction of the feeding line where the sensitive electronic circuitry, used to process the radio frequency signal transmitted or received by the antenna, is located. Secondly, their symmetrical or antipodal radiating structures allow the generation of the symmetrical and stable radiation patterns. Thirdly, they can be fed in both unbalanced and balanced manners. Finally, they can be adopted to realize the antenna arrays, which ensure the gain enhancement. The UWB antenna arrays have been widely used in various microwave through-wall imaging applications. Despite their advantages, the dipole antennas are almost twice the size of the monopole ones. Therefore, it is more reasonable to use the monopole antennas in the compact devices, such as tags.However, the printed monopoles, such as those having the rectangular, circular, elliptical, or triangular shape, can hardly guarantee a frequency band from 3.1 GHz up to 10.6 GHz. In recent years, various impedance matching methods, such as the asymmetric feed technology [7, 8], the external π-shaped matching network [9], and the notched ground [10–12], have been proposed to broaden the bandwidth of conventional monopoles. Furthermore, the band overlapping between the UWB and WLAN may induce the mutual electromagnetic interference. Therefore, the antennas for UWB applications must be designed in such a way to limit or even eliminate the electromagnetic interference with the WLAN communication systems. The C-shaped, T-shaped, and dual U-shaped stubs and slots loaded on the radiation patch [9, 10, 13–16], the defected ground structure (DGS) [17], and the electromagnetic band gap (EBG) [18] have been employed to form a band rejection in an expectant frequency band. Although these antennas have a number of practical advantages, they suffer from some limitations such as the large antenna size and the variation of the radiation patterns at higher frequencies. To overcome these limitations, the antennas with the band notch and stable radiation patterns have attracted more and more attention.This paper presents a novel compact planar two-step beveled UWB antenna. The symmetrical slots integrated on the microstrip line rather than on the radiant patch generate the frequency band notch, while the slots integrated on the ground plane are adopted to improve the radiation patterns. The analysis and design of the proposed antenna have been carried out using 3D full-wave numerical simulation software. The experimental measurements have been shown to be in good agreement with the numerical simulations.


## 2. Antenna Design

### 2.1. Design of the Two-Step Beveled Structure

The geometry of the two-step beveled UWB antenna is shown in Figure1. The dimensions of this antenna, including the low-cost FR4 substrate with the relative dielectric constant of 4.4 and the thickness of 1 mm, are 24 mm × 28 mm. The radiator is printed on the top layer of the substrate, which consists of two differently sized rectangular patches with the chamfered corner of 45°. A microstrip line printed on the top layer is used to feed the radiator centrally. To obtain the characteristic impendence of 50 Ω, the width of the microstrip line, as denoted by W
f, in Figure 1(a), is fixed at 2.2 mm. The truncated ground is printed on the backside of the substrate.Figure 1
Geometry of the two-step beveled antenna: (a) top view and (b) bottom view.This kind of structure can reduce the influence of the discontinuity present in the antenna feeding point, which is achieved by gradually changing the distribution of the current that flows from the feeding line to the radiant patch. In fact, to a certain extent, the smoothness of the current distribution improves the impedance matching. Table1 reports the parameters of the antenna illustrated in Figure 1. The high frequency structure simulator (HFSS) has been employed to perform the antenna design. The simulation results, as illustrated in Figure 2, indicate that the band with the return loss above 10 dB covers the range from 3 GHz to 13 GHz, and thus the ultra-wideband impedance matching is achieved.Table 1
Parameters of the two-step beveled monopole antenna.
Parameters
Value (mm)
Parameters
Value (mm)
W1
20
d1
3
W2
14
d2
2.5
L1
11
G
0.7
L2
5
Lg
9Figure 2
Return loss versus frequency (solid line: the two-step beveled antenna and dash line: the proposed antenna).


### 2.2. Design of the Band-Notched UWB Antenna

According to the standard 802.11a, the frequency band that ranges from 5.15 GHz to 5.825 GHz is licensed to the WLAN, which partially overlaps with the operational band of the UWB communication systems. To reduce the mutual electromagnetic interference, the antennas with the band notches are usually employed in the UWB systems. Two symmetrical slots along with the microstrip line substitute the traditional C-shaped slot embedded in the patch to generate the desired notched band. Figure3(a) depicts the geometry of the proposed antenna.The proposed antenna with the band notch: (a) geometry of the proposed antenna, (b) structure of the SIR, and (c) current distribution at 5.5 GHz.
(a)
(b)
(c)The shape of the slots embedded along with the feeding line looks like a flag, and these flag slots play a role as the stepped impedance resonator (SIR) [19–21]. The SIR is a resonator that is formed by joining two microstrip lines with the characteristic impedances Z
1 and Z
2 as well as the electric lengths θ
1 and θ
2, respectively. Figure 3(b) shows that when Z
1 and Z
2 are equal the characteristic impedance of the resonator is uniform and accordingly a uniform impedance resonator (UIR) is obtained. In particular, the resonance condition of the SIR can be expressed as follows:
(1)
Z
2
-
Z
1
tan
θ
1
tan
θ
2
=
0
.Thus,(2)
tan
θ
1
tan
θ
2
=
Z
2
Z
1
=
K
,
where K denotes the impedance ratio. Compared to the UIR, the SIR can shorten the length of the resonator more effectively at the same resonant frequency by controlling the impedance ratio.In this paper, two symmetrical slot SIRs, with the effective length of approximately half of the wavelength at the frequency of about 5.5 GHz, are adopted to construct the band-notched structure.Near the antenna frequency notch, the dominant current around the notch structure flows in opposite directions as shown in Figure3(c). Consequently, the radiated electric field in the far-field region becomes negligible. This behavior of the surface current explains the formation of the band notch in the frequency range from 5 GHz to 6 GHz.


## 2.1. Design of the Two-Step Beveled Structure

The geometry of the two-step beveled UWB antenna is shown in Figure1. The dimensions of this antenna, including the low-cost FR4 substrate with the relative dielectric constant of 4.4 and the thickness of 1 mm, are 24 mm × 28 mm. The radiator is printed on the top layer of the substrate, which consists of two differently sized rectangular patches with the chamfered corner of 45°. A microstrip line printed on the top layer is used to feed the radiator centrally. To obtain the characteristic impendence of 50 Ω, the width of the microstrip line, as denoted by W
f, in Figure 1(a), is fixed at 2.2 mm. The truncated ground is printed on the backside of the substrate.Figure 1
Geometry of the two-step beveled antenna: (a) top view and (b) bottom view.This kind of structure can reduce the influence of the discontinuity present in the antenna feeding point, which is achieved by gradually changing the distribution of the current that flows from the feeding line to the radiant patch. In fact, to a certain extent, the smoothness of the current distribution improves the impedance matching. Table1 reports the parameters of the antenna illustrated in Figure 1. The high frequency structure simulator (HFSS) has been employed to perform the antenna design. The simulation results, as illustrated in Figure 2, indicate that the band with the return loss above 10 dB covers the range from 3 GHz to 13 GHz, and thus the ultra-wideband impedance matching is achieved.Table 1
Parameters of the two-step beveled monopole antenna.
Parameters
Value (mm)
Parameters
Value (mm)
W1
20
d1
3
W2
14
d2
2.5
L1
11
G
0.7
L2
5
Lg
9Figure 2
Return loss versus frequency (solid line: the two-step beveled antenna and dash line: the proposed antenna).


## 2.2. Design of the Band-Notched UWB Antenna

According to the standard 802.11a, the frequency band that ranges from 5.15 GHz to 5.825 GHz is licensed to the WLAN, which partially overlaps with the operational band of the UWB communication systems. To reduce the mutual electromagnetic interference, the antennas with the band notches are usually employed in the UWB systems. Two symmetrical slots along with the microstrip line substitute the traditional C-shaped slot embedded in the patch to generate the desired notched band. Figure3(a) depicts the geometry of the proposed antenna.The proposed antenna with the band notch: (a) geometry of the proposed antenna, (b) structure of the SIR, and (c) current distribution at 5.5 GHz.
(a)
(b)
(c)The shape of the slots embedded along with the feeding line looks like a flag, and these flag slots play a role as the stepped impedance resonator (SIR) [19–21]. The SIR is a resonator that is formed by joining two microstrip lines with the characteristic impedances Z
1 and Z
2 as well as the electric lengths θ
1 and θ
2, respectively. Figure 3(b) shows that when Z
1 and Z
2 are equal the characteristic impedance of the resonator is uniform and accordingly a uniform impedance resonator (UIR) is obtained. In particular, the resonance condition of the SIR can be expressed as follows:
(1)
Z
2
-
Z
1
tan
θ
1
tan
θ
2
=
0
.Thus,(2)
tan
θ
1
tan
θ
2
=
Z
2
Z
1
=
K
,
where K denotes the impedance ratio. Compared to the UIR, the SIR can shorten the length of the resonator more effectively at the same resonant frequency by controlling the impedance ratio.In this paper, two symmetrical slot SIRs, with the effective length of approximately half of the wavelength at the frequency of about 5.5 GHz, are adopted to construct the band-notched structure.Near the antenna frequency notch, the dominant current around the notch structure flows in opposite directions as shown in Figure3(c). Consequently, the radiated electric field in the far-field region becomes negligible. This behavior of the surface current explains the formation of the band notch in the frequency range from 5 GHz to 6 GHz.


## 3. Antenna Analysis and Design

### 3.1. Effects of the Geometrical Parameters on the Antenna Performance

The parameters of the two-step beveled antenna play a key role on the UWB impedance matching. These parameters are unconstrained variables except ford1, which is equal to half of the difference betweenW1 andW2. In the following, we analyze the effects of the geometrical parameters on the antenna performance. In order to identify the role played by the geometrical parameters on the antenna performance, in the following the trends of the return loss versus the frequency, obtained by varying one parameter at a time while keeping all the others constant, are reported.Figure4 shows the effects of the geometrical parametersL1 andL2 on the antenna frequency band. From the numerical results reported in Figure 4, it is found that the lower and upper frequencies vary weakly as the parameterL1 increases. WhenL2 decreases, the lower and upper frequencies shift toward the higher frequencies simultaneously, and the bandwidth is broadened remarkably. This happens because the parameterL1 is located in the region II that is far away from the edge of the truncated ground plane (see Figure 1) where the electric field is so weak that the parameterL1 has a very small influence on the antenna impedance, while the region I is close to the ground plane and consequently the current distribution is stronger with respect to that excited in the region II. As the parameterL2 decreases, the current path shortens, meaning that the reactive magnetic energy stored near the monopole reduces. Accordingly, the impedance matching at the upper frequency improves.Return loss versus frequency (a) for different values of the parameterL1(other parameters:G = 1 mm,L2 = 8 mm,Lg = 9 mm,W2 = 14 mm,W1 = 20 mm,d1 = 0, andd2 = 0) and (b) for different values of the parameterL2 (other parameters:G = 1 mm,L2 = 11 mm,Lg = 9 mm,W2 = 14 mm,W1 = 20 mm,d1 = 0, andd2 = 0).
(a)
(b)Since the region II weakly contributes to the antenna impedance matching, the analysis with respect to the parameterW1 is not reported. As shown in Figure 5(a), with the decreasing ofW2, the two-step structure is formed. The reactive electric energy excited close to the truncated ground plane neutralizes the reactive magnetic energy excited close to the monopole in the frequency range from 6 GHz to 12 GHz, thus maintaining the antenna reactance at values close to zero. The simulation results illustrated in Figure 6(a) reveal a suitable impedance matching.Return loss versus frequency (a) for different values of the parameterW2 (other parameters:G = 1 mm,L2 = 11 mm,Lg = 9 mm,L2 = 5 mm,W1 = 20 mm,d1 = 0, andd2 = 0) and (b) for different values of the parameterG (other parameters:W2 = 5 mm,L2 = 11 mm,Lg = 9 mm,L2 = 5 mm,W1 = 20 mm,d1 = 0, andd2 = 0).
(a)
(b)Frequency behavior of the real part of the antenna input impedance: (a) antenna without the band notch for different values of the parameterW2, solid line:W2 = 13 mm and dash line:W2 = 16 mm (other parameters:G = 1 mm,L2 = 11 mm,Lg = 9 mm,L2 = 5 mm,W1 = 20 mm,d1 = 0, andd2 = 0,) and (b) antenna with the band notch (other parameters:Lv1 = 13.5 mm,Lv2 = 0 mm,Ln = 4 mm,S = 0.2 mm, andWs = 1 mm).
(a)
(b)The gap between the radiator and the ground, as denotedbyG, is a crucial parameter that determines the electromagnetic coupling. A smaller gap means the tighter capacitive coupling, which further neutralizes the inductive reactance. Figure 5(b) illustrates a better impedance matching.The lengthLg of the truncated ground plane influences the lower frequency of the antenna. In particular, larger values of this parameter reduce this frequency even if this may lead to antennas of higher dimensions. In such a case, a compromise must be made. Considering the antenna size and performance,Lg is fixed at 9 mm. Eventually, the chamfered distanced2 is optimized. All of the optimized parameters are listed in Table 1. The simulated return loss is shown in Figure 2 from which it can be found that the frequency band covers the range from 3 GHz to 13 GHz and meets the requirements of the UWB communication systems.


### 3.2. Effects of the Geometrical Parameters on the Band Notch

Figure7 shows the effects of the parametersLv1 andLn on the notch frequency which decreases asLv1 andLn increase, even though the bandwidth of the stop band is almost constant at approximately 550 MHz, covering the frequency band from 5.18 GHz to 5.73 GHz whenLv1 andLn are equal to 15 mm and 4 mm, respectively. The sum ofLv1 andLn is approximately half of the wavelength of the notch frequency, which determines the resonant frequency of the slot resonator. When two symmetric slots are embedded along with the feed line, the radiation resistance is about zero Ohm in the vicinity of the notch frequency as shown in Figure 6(b). Consequently, the radiation resistance is too small to enable an effective radiation process.Band notch versus frequency (a) for different values of the parameterLv1 (other parameters:Lv2 = 0 mm,Ln = 4 mm,S = 0.2 mm, andWs = 1 mm) and (b) for different values of the parameterLn (other parameters:Lv2 = 0 mm,Lv1 = 13.5 mm,S = 0.2 mm, andWs = 1 mm).
(a)
(b)By changing the slot width, as denoted byS, the quality factor of the slot resonator can be adjusted. Figure 8(a) shows that the bandwidth of the stop band broadens significantly. When S is equal to 0.4 mm, the stop band covers the range from 5.7 GHz to 7 GHz. However, a spurious stop band is also formed. The integer multiples of the parasitic band are an inherent characteristic of UIR. Therefore, the location of the parasitic band can be changed against various impedance ratios of the SIR.Band notch versus frequency (a) for different values of the parameterS (other parameters:Lv2 = 0 mm,Ln = 4 mm,Lv1 = 0.2 mm, andWs = 1 mm) and (b) for different values of the parameterLv2 (other parameters:S = 0.2 mm,Lv1 = 13.5 mm,Ln = 4 mm, andWs = 1 mm).
(a)
(b)Figure8(b) illustrates the effects ofLv2 on the band notch. The impedance ratio of the SIR and the ratio of the second parasitic band to the main resonant frequency increase with the increasing ofLv2. The parasitic band is pushed outside 13 GHz whenLv2 reaches 3 mm.The effects ofWs on the band notch are negligible, and thus an exhaustive analysis is not indispensable. Table 2 reports the optimized parameters of the notch structure whenWs isfixed at 1 mm, and accordingly the notched band covers the range from 5.05 GHz to 6 GHz.Table 2
Optimized parameters of the notch structure.
Parameters
Value (mm)
Parameters
Value (mm)
Lv1
13
S
0.4
Lv2
2.5
Ln
3.6


### 3.3. Optimized Radiation Patterns

The radiation pattern is an important indicator of the antenna performance. Figure9 illustrates the radiation patterns of the antenna depicted in Figure 1. The antenna radiation pattern significantly changes its shape at the upper frequency. In particular, it manifests an increasing cross-polarization effect. The radiation lobe tends to split in theE-plane (XOZ plane), while it loses its circular symmetry in theH-plane (XOY plane). This is due to the unequal surface current phase at a discrete frequency. At the lower frequency of 3.1 GHz, the length of the monopole equals approximately a half wavelength. Furthermore, the longitudinal current is in phase. But at 10 GHz, the physical length of the monopole exceeds a half wavelength, and also the out-phase longitudinal current contribution appears, which results in the null point in the far-field region.Normalized radiation patterns for the antenna without L-shaped slots loaded (solid line: copolar polarization and dash line: cross-polarization).
(a)
3.1 GHzE-plane
(b)
3.1 GHzH-plane
(c)
10 GHzE-plane
(d)
10 GHzH-planeThe current distribution on the finite ground contributes to the radiation too. In order to improve the radiation patterns, two symmetrical L-shaped slots are embedded on the edge of the ground plane. Figure3(a) shows the geometry of the proposed antenna with the band notch and optimized slot parameters.Figure10 shows the improved antenna radiation patterns. At the upper frequency of 10 GHz, the lobe of the radiation pattern in theE-plane splits barely, while the direction of the maximum radiation remains almost the same. The cross-polarization level is greater than 20 dB. The radiation pattern in theH-plane is nearly omnidirectional. Moreover, the cross-polarization level of theH-plane is also improved.Normalized radiation patterns for the proposed antenna (red solid line: measured copolar polarization, black solid line: simulated copolar polarization, red dash line: measured cross-polarization, and black dash line: simulated cross-polarization).
(a)
3.1 GHzE-plane
(b)
3.1 GHzH-plane
(c)
10 GHzE-plane
(d)
10 GHzH-plane


## 3.1. Effects of the Geometrical Parameters on the Antenna Performance

The parameters of the two-step beveled antenna play a key role on the UWB impedance matching. These parameters are unconstrained variables except ford1, which is equal to half of the difference betweenW1 andW2. In the following, we analyze the effects of the geometrical parameters on the antenna performance. In order to identify the role played by the geometrical parameters on the antenna performance, in the following the trends of the return loss versus the frequency, obtained by varying one parameter at a time while keeping all the others constant, are reported.Figure4 shows the effects of the geometrical parametersL1 andL2 on the antenna frequency band. From the numerical results reported in Figure 4, it is found that the lower and upper frequencies vary weakly as the parameterL1 increases. WhenL2 decreases, the lower and upper frequencies shift toward the higher frequencies simultaneously, and the bandwidth is broadened remarkably. This happens because the parameterL1 is located in the region II that is far away from the edge of the truncated ground plane (see Figure 1) where the electric field is so weak that the parameterL1 has a very small influence on the antenna impedance, while the region I is close to the ground plane and consequently the current distribution is stronger with respect to that excited in the region II. As the parameterL2 decreases, the current path shortens, meaning that the reactive magnetic energy stored near the monopole reduces. Accordingly, the impedance matching at the upper frequency improves.Return loss versus frequency (a) for different values of the parameterL1(other parameters:G = 1 mm,L2 = 8 mm,Lg = 9 mm,W2 = 14 mm,W1 = 20 mm,d1 = 0, andd2 = 0) and (b) for different values of the parameterL2 (other parameters:G = 1 mm,L2 = 11 mm,Lg = 9 mm,W2 = 14 mm,W1 = 20 mm,d1 = 0, andd2 = 0).
(a)
(b)Since the region II weakly contributes to the antenna impedance matching, the analysis with respect to the parameterW1 is not reported. As shown in Figure 5(a), with the decreasing ofW2, the two-step structure is formed. The reactive electric energy excited close to the truncated ground plane neutralizes the reactive magnetic energy excited close to the monopole in the frequency range from 6 GHz to 12 GHz, thus maintaining the antenna reactance at values close to zero. The simulation results illustrated in Figure 6(a) reveal a suitable impedance matching.Return loss versus frequency (a) for different values of the parameterW2 (other parameters:G = 1 mm,L2 = 11 mm,Lg = 9 mm,L2 = 5 mm,W1 = 20 mm,d1 = 0, andd2 = 0) and (b) for different values of the parameterG (other parameters:W2 = 5 mm,L2 = 11 mm,Lg = 9 mm,L2 = 5 mm,W1 = 20 mm,d1 = 0, andd2 = 0).
(a)
(b)Frequency behavior of the real part of the antenna input impedance: (a) antenna without the band notch for different values of the parameterW2, solid line:W2 = 13 mm and dash line:W2 = 16 mm (other parameters:G = 1 mm,L2 = 11 mm,Lg = 9 mm,L2 = 5 mm,W1 = 20 mm,d1 = 0, andd2 = 0,) and (b) antenna with the band notch (other parameters:Lv1 = 13.5 mm,Lv2 = 0 mm,Ln = 4 mm,S = 0.2 mm, andWs = 1 mm).
(a)
(b)The gap between the radiator and the ground, as denotedbyG, is a crucial parameter that determines the electromagnetic coupling. A smaller gap means the tighter capacitive coupling, which further neutralizes the inductive reactance. Figure 5(b) illustrates a better impedance matching.The lengthLg of the truncated ground plane influences the lower frequency of the antenna. In particular, larger values of this parameter reduce this frequency even if this may lead to antennas of higher dimensions. In such a case, a compromise must be made. Considering the antenna size and performance,Lg is fixed at 9 mm. Eventually, the chamfered distanced2 is optimized. All of the optimized parameters are listed in Table 1. The simulated return loss is shown in Figure 2 from which it can be found that the frequency band covers the range from 3 GHz to 13 GHz and meets the requirements of the UWB communication systems.


## 3.2. Effects of the Geometrical Parameters on the Band Notch

Figure7 shows the effects of the parametersLv1 andLn on the notch frequency which decreases asLv1 andLn increase, even though the bandwidth of the stop band is almost constant at approximately 550 MHz, covering the frequency band from 5.18 GHz to 5.73 GHz whenLv1 andLn are equal to 15 mm and 4 mm, respectively. The sum ofLv1 andLn is approximately half of the wavelength of the notch frequency, which determines the resonant frequency of the slot resonator. When two symmetric slots are embedded along with the feed line, the radiation resistance is about zero Ohm in the vicinity of the notch frequency as shown in Figure 6(b). Consequently, the radiation resistance is too small to enable an effective radiation process.Band notch versus frequency (a) for different values of the parameterLv1 (other parameters:Lv2 = 0 mm,Ln = 4 mm,S = 0.2 mm, andWs = 1 mm) and (b) for different values of the parameterLn (other parameters:Lv2 = 0 mm,Lv1 = 13.5 mm,S = 0.2 mm, andWs = 1 mm).
(a)
(b)By changing the slot width, as denoted byS, the quality factor of the slot resonator can be adjusted. Figure 8(a) shows that the bandwidth of the stop band broadens significantly. When S is equal to 0.4 mm, the stop band covers the range from 5.7 GHz to 7 GHz. However, a spurious stop band is also formed. The integer multiples of the parasitic band are an inherent characteristic of UIR. Therefore, the location of the parasitic band can be changed against various impedance ratios of the SIR.Band notch versus frequency (a) for different values of the parameterS (other parameters:Lv2 = 0 mm,Ln = 4 mm,Lv1 = 0.2 mm, andWs = 1 mm) and (b) for different values of the parameterLv2 (other parameters:S = 0.2 mm,Lv1 = 13.5 mm,Ln = 4 mm, andWs = 1 mm).
(a)
(b)Figure8(b) illustrates the effects ofLv2 on the band notch. The impedance ratio of the SIR and the ratio of the second parasitic band to the main resonant frequency increase with the increasing ofLv2. The parasitic band is pushed outside 13 GHz whenLv2 reaches 3 mm.The effects ofWs on the band notch are negligible, and thus an exhaustive analysis is not indispensable. Table 2 reports the optimized parameters of the notch structure whenWs isfixed at 1 mm, and accordingly the notched band covers the range from 5.05 GHz to 6 GHz.Table 2
Optimized parameters of the notch structure.
Parameters
Value (mm)
Parameters
Value (mm)
Lv1
13
S
0.4
Lv2
2.5
Ln
3.6


## 3.3. Optimized Radiation Patterns

The radiation pattern is an important indicator of the antenna performance. Figure9 illustrates the radiation patterns of the antenna depicted in Figure 1. The antenna radiation pattern significantly changes its shape at the upper frequency. In particular, it manifests an increasing cross-polarization effect. The radiation lobe tends to split in theE-plane (XOZ plane), while it loses its circular symmetry in theH-plane (XOY plane). This is due to the unequal surface current phase at a discrete frequency. At the lower frequency of 3.1 GHz, the length of the monopole equals approximately a half wavelength. Furthermore, the longitudinal current is in phase. But at 10 GHz, the physical length of the monopole exceeds a half wavelength, and also the out-phase longitudinal current contribution appears, which results in the null point in the far-field region.Normalized radiation patterns for the antenna without L-shaped slots loaded (solid line: copolar polarization and dash line: cross-polarization).
(a)
3.1 GHzE-plane
(b)
3.1 GHzH-plane
(c)
10 GHzE-plane
(d)
10 GHzH-planeThe current distribution on the finite ground contributes to the radiation too. In order to improve the radiation patterns, two symmetrical L-shaped slots are embedded on the edge of the ground plane. Figure3(a) shows the geometry of the proposed antenna with the band notch and optimized slot parameters.Figure10 shows the improved antenna radiation patterns. At the upper frequency of 10 GHz, the lobe of the radiation pattern in theE-plane splits barely, while the direction of the maximum radiation remains almost the same. The cross-polarization level is greater than 20 dB. The radiation pattern in theH-plane is nearly omnidirectional. Moreover, the cross-polarization level of theH-plane is also improved.Normalized radiation patterns for the proposed antenna (red solid line: measured copolar polarization, black solid line: simulated copolar polarization, red dash line: measured cross-polarization, and black dash line: simulated cross-polarization).
(a)
3.1 GHzE-plane
(b)
3.1 GHzH-plane
(c)
10 GHzE-plane
(d)
10 GHzH-plane


## 4. Fabrication and Measurement

The fabricated antenna, designed according to the methodology described above, is shown in Figure11. The measurement results have been performed by using the Agilent N5232A vector network analyzer. The comparison between the experimental and simulation results in terms of the return loss is illustrated in Figure 12. From the experimental measurements, it is found that the band-notched filter covers the frequency range from 5.05 GHz up to 5.95 GHz. The measured notched band is less than the simulated one covering the range from 5.05 GHz to 6.05 GHz. The measured lower frequency with the return loss of 10 dB is 3.24 GHz, while that obtained via the numerical simulations is about 3.02 GHz. Such a deviation between the measurement and simulation results comes from the machining and permittivity tolerances, as well as from the irregular soldering whose perturbative effects are more evident at the higher frequencies. Finally, the measurement of the antenna peak gain is reported in Figure 13. This figure shows that the peak gain is about 2.5 dBi~3.6 dBi at the lower frequency, 3 dBi~4.5 dBi at the upper frequency, and below 0 dBi in the frequency band 5 GHz~6 GHz. The group delay properly quantifies the propagation properties of the so-called wave packet [2]. The signal integrity is confirmed by analyzing the relative group delay τ
grel
(
ω
), which is defined as
(3)
τ
grel
(
ω
)
=
τ
g
(
ω
)
-
τ
-
g
,
where
(4)
τ
g
(
ω
)
=
-
d
ϕ
(
ω
)
d
ω
,
denotes the group delay and ϕ
(
ω
) represents the phase of the radiated electromagnetic field. In (3), τ
-
g denotes the mean value of the relative group delay that has been evaluated at a distance of 50 cm from the center of the proposed antenna along the X-axis. Figure 14 shows that the variations of the measured group delay are less than one nanosecond throughout the operational band expect in the band notch. These results indicate that the antenna has the good linear transmission performance and can be used in the multiband or impulse UWB radio applications.Prototype of the proposed antenna: (a) top view and (b) bottom view.
(a)
(b)Figure 12
Comparison between the measured and simulated return losses.Figure 13
Peak gain of the proposed antenna (red solid line: measured gain and black solid line: simulated gain).Figure 14
Frequency-domain behavior of the group delay.


## 5. Conclusion

A compact two-step beveled printed monopole antenna with the WLAN band-notch characteristic has been proposed in this paper. The effects of the geometrical parameters on the antenna performance have been investigated. A two-step structure has been utilized to broaden the bandwidth of the antenna impedance, while the slots embedded in the metal patch have been adopted to realize the notch band. By changing the parameters of the notch structure, the notch frequency and its bandwidth are controllable without perturbing the remaining part of the UWB band. In order to improve the shape of the radiation patterns at the upper frequency, two L-shaped slots have been integrated on the edge of the ground plane. Since the proposed antenna presents a compact structure (the overall size of the antenna is 24 mm × 28 mm) and a stable radiation pattern, it is able to be effectively utilized in the UWB radio communication systems.



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*Source: 173704-2014-05-27.xml*