Abstract:
A nine-phase AC to DC power converter system may exhibit current unbalance problem among bridges due to two reasons: slight voltage magnitude difference among different sets of three-phase supplies and pre-existing voltage harmonics in the power supply lines. Since the unpredictability of the pre-existing harmonics and manufacturing uncertainty of the nine-phase power supply (it is usually a three to nine phase transformer), all devices in the rectifier bridges are required to carry much higher than necessary current magnitude and have to be designed oversize, as much as 100% up. Here we describe various topologies of harmonic blocking reactors to combat this problem. The described topologies can significantly improve this situation and thus avoid the over-sizing exercise (cost) when such converter system is built. The principle can be easily extended to any multi-phase AC to DC or DC to AC power conversion system of more than nine phases. The principle can be extended to any multi-phase converter system with more than nine phases.

Description:
CROSS-REFERENCE TO RELATED APPLICATIONS 
     Not applicable. 
     STATEMENT REGARDING FEDERALLY SPONSORED RESEARCH OR DEVELOPMENT 
     Not applicable. 
     BACKGROUND OF THE INVENTION 
     The field of the invention is AC to DC converter systems and more specifically a blocking reactor including three cores for blocking harmonic currents in a nine-phase converter system. 
     Rectifiers are used to rectify AC voltages and generate DC voltages across DC buses. A typical rectifier includes a switch-based bridge including two switches for each AC voltage phase which are each linked to the DC buses. The switches are alternately opened and closed in a timed fashion that, as the name implies, causes rectification of the AC voltage. As well known in the energy industry the global standard for AC power distribution is three-phase and therefore three-phase rectifier bridges are relatively common. 
     When designing a rectifier configuration there are three main considerations including cost, AC line current harmonics and DC bus ripple. With respect to AC current harmonics, when an AC phase is linked to a rectifier and rectifier switches are switched, the switching action is known to cause harmonics on the AC lines. AC line harmonics caused by one rectifier distort the AC voltages provided to other commonly linked loads and therefore should generally be limited to the extent possible. In fact, specific applications may require that large rectifier equipment be restricted in the AC harmonics that the equipment produces. 
     With respect to DC link ripple, rectifier switching typically generates ripple on the DC bus. With respect to cost, as with most hardware intensive configurations, cost can be minimized by using a reduced number of system components and using relatively inexpensive components where possible. 
     The most common and available type AC to DC converter is a three-phase rectifier system including six semiconductor switches arranged to form a converter that links three AC input lines to positive and negative DC buses where the voltage on the input lines is spaced by 120 electrical degrees. This type of six-switch converter system exhibits relatively high DC output voltage ripple at a frequency that is six times the AC line frequency. For example, where the line frequency is 60 Hertz, the ripple is typically 360 Hertz. Converters that include six switches are generally referred to as six-pulse rectifiers. 
     It is well known in AC to DC rectification that AC current harmonics and DC ripple may be improved by increasing the number of AC phases that are rectified where the AC phases are phase-shifted from each other. For example, by rectifying nine-phase AC current instead of three-phase currents, harmonics and ripple are reduced appreciably. To rectify nine phase currents the industry most solutions employ three three-phase rectifiers, each of the three rectifiers including six switches arranged to form a bridge between each of three of the AC supply lines and DC rectifier outputs. The outputs can be linked in several different fashions to provide one positive DC bus and one negative DC bus as described in more detail below. Three rectifier configurations that include a total of 18 switches are generally referred to as 18 pulse rectifiers. 
     As the global standard for AC power distribution is three-phase, a mechanism for converting three-phase current to nine-phase current is necessary prior to rectification via any 18-pulse rectifier. To this end the industry has devised several different three to nine-phase transformer configurations. An exemplary three to nine-phase transformer and rectifier configuration is illustrated in FIG. 1 including a transformer  100 , and first, second and third rectifiers  120 ,  140  and  160 , respectively, that link three AC supply lines  122 ,  124  and  126  to positive and negative DC buses  128  and  180 , respectively. Transformer  100  receives three 120 degree phase shifted AC currents I A , I B  and I C  on input lines  122 ,  124  and  126  and provides nine AC output currents I 1  through I 9  on nine AC output lines (not numbered) where the output currents include three currents I 4 -I 6  that are in phase with the input currents, three currents I 1 -I 3  that lag the input currents by 20 degrees and three currents I 7 -I 8  that lead the input currents by 20 degrees. 
     Currents I 1  through I 3 , currents I 4  through I 6  and currents I 7  through I 9  are provided to rectifiers  120 ,  140  and  160 , respectively. The outputs of rectifiers  120 ,  140  and  160  are linked together in parallel. The rectifier input currents I 1 -I 9  are summed together to produce a primary current I A  through I C  having reduced harmonics. Because the pre-rectified voltages V 1 -V 3 , V 4 -V 6  and V 7 -V 9  are spaced out 20 degrees, their rectified DC voltages fill each other&#39;s valleys and hence produce an 18 times fundamental frequency ripple that is relatively smoother when compared to six-switch configurations. 
     In theory 18 pulse systems like the one illustrated in FIG. 1 have the advantage that each rectifier needs only include components having a power rating corresponding to one third the overall DC output power rating. Thus, in theory 18-pulse rectifier switches in parallel linked configurations can be one third the size of switches required for six pulse rectifiers. 
     In reality, however, for two reasons the rectifier components have to be greater than the theoretical one-third rated DC size. First, due to manufacturing limitations, slight magnitude differences occur in most cases among the rectifier input voltages. These slight voltage magnitude differences produce slight DC voltage differences at each of the separate rectifier outputs. For example, DC output voltage variance among rectifier outputs is often within the range of 0 to 2 volts. 
     Converter systems are typically constructed for very low impedance to provide a stiff voltage source to a load. For this reason the slight differences in DC voltage, although small in most cases, cause the rectifier with highest output DC voltage to carry much more DC load current when compared with the current carried by the other rectifiers. 
     Second, referring again to FIG. 1, in a typical application the three-phase power source would be linked to many loads like the one illustrated and each of those loads would cause some degree of harmonic distortion on supply lines  122 ,  124  and  126 . As known in the industry, the rectified DC voltage for a single three-phase bridge with pre-existing 5 th  and 7 th  harmonics is:                V     d                 c       =         3        3         2      π              V   1          (     1   -       1   5            V   5       V   1          cos                   φ   5       -       1   7            V   7       V   1          cos                   φ   7         )                 Eq   .              1                                
     with 
     
       
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     Equation 1 indicates that both the magnitude and angle of the harmonic voltages influence the DC voltage. As obvious from FIG. 1, the rectifier input voltages V 1 -V 3 , V 4 -V 6  and V 7 -V 9  are spaced out 20 degrees. Thus the values of the harmonic angles (see Equations 1 through 4) for each rectifier  12 ,  14  and  16 , are changed causing the rectified DC voltages from each rectifier to be different. Thus, the pre-existing harmonics also contribute to current unbalance among different rectifiers. 
     In order to avoid such unbalance problem, one solution is to connect all three bridges in series, instead of in parallel. Referring again to FIG. 1, this type of configuration would include a link between the lower DC output of rectifier  120  and the upper output of rectifier  140 , a link between the lower DC output of rectifier  140  and the upper DC output of rectifier  160  and the DC output buses would include the top and bottom DC output leads of rectifiers  120  and  160 , respectively. In this case, to achieve the DC output voltage level provided by the parallel configuration described above, the magnitude of each nine-phase voltage V 1 -V 9  would only have to be one-third that of the parallel configuration. Unfortunately, each rectifier  120 ,  140  and  160  would have to carry the full rated current and therefore the switching devices therein would have to be full-size and relatively expensive. 
     Other attempts to solve the unbalance problems have employed inter-phase transformers (IPT) having six separate cores between the rectifiers and the DC output rails in parallel rectifier configurations. Unfortunately, with these configurations, each IPT must carry the full DC current generated by the rectifier linked thereto and therefore each IPT must include an air gap adjustment which means that each IPT would be relatively large. In conversion systems where space is limited such excessive space requirements are impractical. 
     In addition, when one of the rectifiers is out of service for any reason (e.g., a fault condition occurs), the four IPTs corresponding to the other two bridges automatically go into saturation which nullifies the effect of the IPTs entirely. 
     Yet other attempts to avoid unbalance problems in parallel rectifier configurations have employed harmonic blocking reactors on the AC side of the rectifiers. For example, some efforts have resulted in configurations including three separate reactors that cancel various (e.g., 5 th  and 7 th ) voltage harmonics for a six-phase DC to AC system. Other efforts have taught that harmonics in a nine-phase system can be cancelled by adjusting different turn ratios among windings in each of six separate reactors. An exemplary nine phase AC side reactor configuration is illustrated in FIG.  2 . In these cases, advantageously, the reactor cores do not need to carry fundamental flux and do not have the saturation problems associated with IPTS. Unfortunately configurations, like the configuration of FIG. 2, that employ AC side reactors have not proven to be much better than the IPT attempts as each attempt requires six separate cores that render required hardware bulky and relatively expensive. 
     Another AC side reactor configuration is taught by U.S. Pat. No. 4,204,264 in FIG.  3  and includes two separate three-phase cores for a nine-phase AC to DC system. Here instead of using six separate cores as in FIG. 2, six limbs from the two separate cores are employed. While a better effort, this two-core solution still requires a relatively large amount of material to accommodate a nine-phase converter system. In addition, because three-phase cores are used triple harmonic fluxes cannot circulate within the core and the configuration therefore does not eliminate the triple harmonics. Thus, it would be advantageous to configure an AC side harmonic blocking reactor that requires a reduced set of cores, reduces triple harmonics and for which saturation is not a problem. 
     BRIEF SUMMARY OF THE INVENTION 
     The present invention is a reactor for linking a multiphase transformer to a rectifier, where the multiphase transformer generates a multiphase AC output signal comprising a plurality of three phase signals. Each of the three phase signals comprises a first, a second and a third output current of substantially similar magnitude, and each of the first, second, and third output currents are spaced one hundred and twenty degrees apart. The first, second, and third output currents of each of the three phase signals are offset from the first, second, and third output currents of another of the three phase signals by a predetermined angle, respectively. The rectifier is for receiving and rectifies the multiphase AC output signals to provide positive and negative DC bus currents. The reactor comprises first, second and third cores and a plurality of winding subsets, the plurality of winding subsets being equal in number to the plurality of three phase signals. Each winding subset includes at least first, second and third windings linked to the first, second and third outputs of the corresponding three phase signal. The windings are arranged on the cores such that at least a winding segment from each of the plurality of winding subsets is wound about each of the first, second and third cores. 
     In one embodiment of the invention the transformer generates AC output currents having substantially similar magnitudes on each of nine outputs. The first, second and third output currents spaced one hundred and twenty degrees apart, the fourth, fifth and sixth output currents leading the first, second and third output currents by a predetermined angle, respectively, the seventh, eighth and ninth output currents lag the first, second and third output currents by substantially the predetermined angle, respectively. The rectifier receives and rectifies nine phase AC currents to provide positive and negative DC bus currents. The reactor comprises three cores and three winding subsets. The first winding subset includes at least first, second and third windings linked to the first, second and third outputs. The second winding subset including at least first, second and third windings linked to the fourth, fifth and sixth outputs. The third winding subset including at least first, second and third windings linked to the seventh, eighth and ninth outputs. The windings arranged on the cores such that at least a winding segment from each of the first, second and third winding subsets is wound about each of the first, second and third cores. 
     The windings of the harmonic reactor of the present invention are preferably sized and dimensioned such that, when receiving AC currents at a fundamental frequency, current passing through each winding generates flux within the core such that the fundamental fluxes through the core cancel. The reactor, however, provides impedance to higher order harmonics, thereby providing a blocking function. 
     In one embodiment of the invention, the reactor is preferably wound such that each of the first, second and third subset first windings are wound about the first core, the first, second and third subset second windings are wound about the second core and the first, second and third subset third windings are wound about the third core. The ratio of the first subset windings to the second and third subset windings on each core is one to one over two times the cosine of the predetermined angle. For a predetermined angle of twenty degrees, and the ratio of first subset windings to second and third subset windings on each core is substantially 1:0.532:0.532. 
     In another embodiment of the invention, the reactor can be configured such that the first subset first winding, the second subset second winding and the third subset third winding are wound about the first core, the first subset second winding, the second subset third winding and the third subset first winding are wound about the second core and the first subset third winding, the second subset first winding and the third subset second winding are wound about the third core. Again, the ratio of the first subset windings to the second and third subset windings on each core is one to one over two times the cosine of two times the predetermined angle. Here for a predetermined angle of substantially 20 degrees, the ratio of first subset windings to second and third subset windings on each core is substantially 1:0.6527:0.6527. 
     The reactor of the present invention can also be configured such that the first winding subset includes a single coil, while the second and third winding subsets include first and second coils. Here the first subset first winding, first coil of the second subset first winding, first coil of the second subset second winding, first coil of the third subset first winding and first coil of the third subset third winding are each wound about the first core. The first subset second winding, second coil of the second subset second winding, first coil of the second subset third winding, second coil of the third subset first winding and first coil of the third subset second winding are wound about the second core. The first subset third winding, second coil of the second subset first winding, second coil of the second subset third winding, second coil of the third subset second winding and second coil of the third subset third winding are wound about the third core. 
     In this embodiment, the reactor can be configured such that the turns ratios of the first subset first winding to the second subset first winding first coil, second subset second winding first coil, third subset first winding first coil and third subset third winding first coil are two to one over two times the cosine of the phase angle between the current linked to the first subset first winding and the current linked to the respective coil. The turns ratios of the first subset second winding to the second subset second winding second coil, second subset third winding first coil, third subset first winding second coil and third subset second winding first coil are two to one over two times the cosine of the phase angle between the current linked to the first subset second winding and the current linked to the respective coil. The turns ratios of the first subset third winding to the second subset first winding second coil, second subset third winding second coil, third subset second winding second coil and third subset third winding second coil are two to one over two times the cosine of the phase angle between the current linked to the first subset first winding and the current linked to the respective coil. This configuration is dimensioned to cancel fundamental flux in each core. 
     For a predetermined angle of twenty degrees, the turns ratio of the first subset first winding to second subset first winding first coil and second winding first coil is substantially 2:0.532:0.6527, respectively. The turns ratio of the first subset first winding to third subset first winding first coil and third winding first coil is substantially 2:0.532:0.6527, the turns ratio of the first subset second winding to second subset second winding second coil and third winding first coil is substantially 2:0.532:0.6527, respectively, the turns ratio of the first subset second winding to third subset first winding second coil and second winding first coil is substantially 2:0.532:0.6527, the turns ratio of the first subset third winding to second subset first winding second coil and third winding second coil is substantially 2:0.6527:0.532, respectively, and the turns ratio of the first winding second coil is substantially 2:0.6527:0.532. 
     The reactor of the present invention can also be configured such that each core forms at least one continuous flux path. The cores can be configured as a single or double window, or to include a first, second and third cores forming first, second and third limbs on a four limb core configuration. In this configuration each limb includes first and second ends wherein, each of the first ends are linked and each of the second ends are linked. 
     These and other objects, advantages and aspects of the invention will become apparent from the following description. In the description, reference is made to the accompanying drawings which forma part hereof, and in which there is shown a preferred embodiment of the invention. Such embodiment does not necessarily represent the full scope of the invention and reference is made therefore, to the claims herein for interpreting the scope of the invention. 
    
    
     BRIEF DESCRIPTION OF THE SEVERAL VIEWS OF THE DRAWINGS 
     FIG. 1 is a block diagram of an eighteen pulse power converter system; 
     FIG. 2 is a prior art harmonic blocking reactor employing AC side reactors; 
     FIG. 3 is another prior art harmonic blocking reactor employing AC side reactors; 
     FIG. 4 is a blocking diagram of a power converter system including a harmonic blocking reactor constructed in accordance with the present invention; 
     FIG. 5 is a vector diagram illustrating the polar distribution of the nine phase ac signal produced by the three to nine phase transformer of FIG. 4; 
     FIG. 6 a  is an illustration of a single window core for use in a harmonic blocking reactor constructed in accordance with the present invention; 
     FIG. 6 b  is an illustration of a double window core for use in a harmonic blocking reactor constructed in accordance with the present invention 
     FIG. 6 c  is an illustration of a four limb core for use in a harmonic blocking reactor constructed in accordance with the present invention 
     FIG. 7 is a block diagram of a first embodiment of a harmonic blocking reactor constructed in accordance with the present invention; 
     FIG. 8 is a vector diagram illustrating the amp turn linkage on a first core of the harmonic blocking reactor of FIG. 7; and 
     FIG. 9 is a block diagram of a second embodiment of a harmonic blocking reactor constructed in accordance with the present invention. 
     FIG. 10 is a vector diagram illustrating the amp turn linkage on a first core of the harmonic blocking reactor of FIG. 9; and 
     FIG. 11 is a block diagram of a third embodiment of a harmonic blocking reactor constructed in accordance with the present invention. 
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     Referring now to the Figures, and more particularly to FIG. 4, a block diagram of a power converter system  10  employing a harmonic blocking reactor  14  constructed in accordance with the present invention is shown. The power converter system  10  preferably comprises a multiphase transformer  12 , harmonic blocking reactor  14 , and rectifier circuit  16 . The application will be described with reference to an eighteen pulse system, as described above. In this case, the multiphase transformer  12  is a three to nine phase transformer. It will be apparent, however, that the multiphase transformer can produce a twelve, fifteen, eighteen, or other multiple&#39;s of a three phase system. Regardless of the number of phases associated with the multiphase transformer  12 , the transformer  12 , harmonic blocking reactor  14 , and rectifier circuit  16  are linked together to convert a three phase AC input  18  to a DC output signal  20 , as will be described more fully below. 
     The three to nine phase transformer  12  receives the three phase AC input signal  18  and converts the signal to a nine phase signal comprising nine ac signals ( 22   a-c ,  24   a-c , and  26   a-c ) of substantially equivalent magnitude at nine separate phase angles. The first, second, and third ac signals,  22   a - 22   c , are preferably spaced substantially one hundred and twenty degrees apart. Each of the fourth, fifth, and sixth signals,  24   a - 24   c , lag the first, second and third ac signals  22   a - 22   c  by a predetermined angle, respectively, and the seventh, eighth and ninth signals  26   a - 26   c , lead the first, second and third ac signals by a substantially similar predetermined angle. The predetermined angle can be an angle of twenty degrees, as shown in the vector diagram of FIG.  5 . However, it will be apparent to those of ordinary skill in the art that different angles can be produced by the three to nine phase transformer, and that the harmonic blocking reactor  14  of the present invention can be configured to accept signals at a number of varying phase angles. Hereafter the first, second, and third ac signals  22   a-c  may be referred to as the first set of ac signals  22 , the fourth, fifth, and sixth ac signals  24   a-c  may be referred to as the second set of ac signals  24 , and the seventh, eight, and ninth ac signals  26   a - 26   c  may be referred to as the third set of ac signals  26 . 
     The harmonic blocking reactor  14  comprises a first, a second, and a third winding subset  28 ,  30 , and  32 , respectively, and a first, a second, and a third core  34 ,  36 , and  38 , respectively. The winding subsets  28 ,  30 , and  32  each comprise at least a first, a second, and a third winding  28   a-c ,  30   a-c , and  32   a-c , respectively (see FIGS. 7,  9  and  11 ). Each winding comprises an input end  29   a-c ,  33   a-c , and  37   a-c , and an output end  31   a-c ,  35   a-c , and  39   a-c , respectively. The windings  28   a-c ,  30   a-c , and  32   a-c  can each comprise a single coil (FIG.  7 ), or, in some applications, can include a first and a second coil linked in series, as will be described with reference to specific embodiments below (FIG.  11 ). It will be apparent to those of ordinary skill in the art that the number of winding subsets are determined based on the number of sets of three phase signals produced by the transformer  12 . Thus, for example, when the multiphase transformer is a three to twelve phase transformer, a fourth winding subset comprising first, second, and third windings is required. 
     The cores  34 ,  36 , and  38  can be constructed in a number of known ways, but preferably comprise laminated steel. Although a number of different shapes can also be used, each core is preferably in the shape of either a single window, or a double window with a central limb, as shown in FIGS. 6 a  and  6   b . In either application, to achieve maximum coupling, the windings are preferably wound along only one limb. An alternative core is shown in FIG. 6 c . Here, the core has four limbs. Three of the limbs are used for windings and the remaining limb is used for individual flux passage. When the four limb core is used, a single core can be used rather than the three cores  34 ,  36 , and  38  shown in FIG.  4 . In the following discussion, however, three separate cores  34 ,  36 , and  38  will be assumed. 
     In the harmonic blocking reactor  14 , at least one coil of the first, second, and third windings  28   a - 28   c  of the first winding subset  28  is coupled to each of the first, second, and third cores  34 ,  36 , and  38 , respectively; at least one coil of the first, second, and third windings  30   a - 30   c  of the second winding subset  30  is coupled to each of the first, second, and third cores  34 ,  36 , and  38 , respectively; and at least one coil of the first, second, and third windings  32   a - 32   c  of the third winding subset  32  is coupled to each of the first, second, and third cores  34 ,  36 , and  38 , respectively. The windings coupled to each core  34 ,  36 , and  38  are sized and dimensioned such that the flux induced in each of the cores  34 ,  36 , and  38  cancels at the fundamental frequency, thereby providing an impedance of zero to signals at the fundamental frequency. The harmonic blocking reactor  14 , however, provides an impedance to components of input signals at the higher harmonics, as described more fully below. Again, the theory as described is easily extended to a twelve phase or higher system. In this case, at least one winding from each additional winding subset is wound about each of the three cores  34 ,  36 , and  38 , and the windings are sized and dimensioned to cancel fundamental frequency at each core. 
     In the power converter system  10 , each of the first set of ac input signals  22   a-c  is linked to the input end  29   a-c  of the first subset of windings  28   a-c  of the harmonic blocking reactor  14 , respectively. Each of the second set of ac input signals  24   a-c  is coupled to the input end  33   a-c  of the second subset of windings  30   a-c , respectively, and each of the third set of ac input signals  26   a-c  is coupled to the input end  37   a-c  of the third subset of windings  32   a-c , respectively. The output of the harmonic blocking reactor  14  is a nine phase ac output signal ( 40   a-c ,  42   a-c , and  44   a-c ), wherein each of these signals is associated with the output ends ( 31   a-c ,  35   a-c ,  39   a-c ) of the three winding subsets  28 ,  30 , and  32 , respectively. 
     The rectifier  16  receives nine phase ac output signal  40   a-c ,  42   a-c , and  44   a-c from the harmonic blocking reactor  14  and converts these signals to the dc signal  20 . Preferably, the rectifier circuit  16  comprises three separate rectifiers  16   a ,  16   b , and  16   c , each of which receives and rectifies three of the nine ac output signals. The outputs  20   a ,  20   b , and  20   c  of each of the rectifiers  16   a ,  16   b , and  16   c  are tied together in a parallel configuration such that each of the rectifiers carries only one third of the total current in the power converter system  10 . The parallel configuration allows the use of smaller rectifier components, thereby helping to reduce the size of the power converter system  10 . 
     Referring now to FIG. 7, a first embodiment of a harmonic blocking reactor  14  constructed in accordance with the present invention is shown. The harmonic blocking reactor  14  comprises three cores  34 ,  36 , and  38 , as well as three winding subsets  28 ,  30 , and  32 . Each winding subset comprises first, second, and third windings  28   a-c ,  30   a-c , and  32   a-c , respectively, and each of the windings  28   a-c ,  30   a-c , and  32   a-c  comprises a single coil  28   a′-c ′,  30   a′-c ′, and  32   a′-c ′, respectively. 
     In this embodiment, the first, second, and third ac signals  22   a ,  22   b , and  22   c  are linked to the first, second, and third windings  28   a ,  28   b , and  28   c  of the first winding subset  28 . Similarly, the fourth, fifth, and sixth ac signals  24   a ,  24   b , and  24   c  are linked to the first, second, and third windings  30   a ,  30   b , and  30   c  of the second winding subset  30  and the seventh, eighth, and ninth ac signals  26   a ,  26   b , and  26   c  are linked to the first, second, and third windings  32   a ,  32   b , and  32   c  of the third winding subset  30 . The first winding ( 28   a ,  30   a , and  32   a  ) from each of the winding subsets  28 ,  30 , and  32  is wound around the first core  34 , the second winding ( 28   b ,  30   b , and  32   b  ) from each of the winding subsets  28 ,  30 , and  32  is wound around the second core  36 , and the third winding ( 28   c ,  30   c , and  32   c  ) from each of the winding subsets  28 ,  30 , and  32  is wound around the third core  38 . 
     Referring again to FIG. 7, the ac signals coupled to the windings wound about each of the cores  34 ,  36 , and  38  include one ac signal from the first set of ac signals  22 , one from the second set of ac signals  24 , and one from the third set of ac signals  26 . For each core  34 ,  36 , and  38 , the ac signals from the second and third set of ac signals are selected to be the closest signals to the ac signal from the first set of ac signals  22 . For example, for a nine phase input signal constructed as shown in FIG. 5, the ac signals coupled to the windings wound about the core  34 , for example, include the signals  22   a  (zero degrees),  24   a  (twenty degrees) and  26   a  (negative twenty degrees). The windings wound around the cores  36  and  38  each also comprise three ac signals offset from each other by an angle of twenty degrees. 
     The winding turn ratio of the coils wound about each core  34 ,  36 , and  38 , is selected to cancel fundamental flux in the respective core. A vector diagram illustrating the cancellation of fundamental flux in the core  34  with the harmonic blocking reactor of FIG. 7 is shown in FIG.  8 . Here, the coils wound around the core  34  are the coils  28   a ′,  30   a ′, and  32   a ′. Since the magnitude of the current flow of the ac signals in each of the coils is substantially equivalent, the turn ratio of the coils  28   a ′,  30   a ′, and  32   a ′ must be dimensioned such that the sum of the amp turn vectors associated with each of the coils  28   a ′,  30   a ′, and  32   a ′ is zero. The amp turn vectors are the product of the current flow into the coil (i x ) and the number of turns in a given coil (N x ). To achieve zero flux at fundamental frequency, the ampere turns N 30a i 24a  and N 32a i 26a  are constructed such that they form a loop against N 28a i 22a , as shown in FIG.  8 . In general, the required turn winding ratio is:                  N     30        a   ′           N     28        a   ′           =         N     32        a   ′           N     29        a   ′           =     1     2      cos                 θ                 Eq   .              5                                
     where θ is the phase angle between the signals coupled to the windings on each core. For the specific embodiment where the fourth, fifth and sixth ac signals  24   a-c  lead the first, second, and third ac signals  22   a-c  by an angle of twenty degrees and the seventh, eighth, and ninth ac signals  26   a-c  lag the first, second, and third ac signals by an angle of twenty degrees, as shown in FIG. 3, the winding turn ratio is:                  N     30        a   ′           N     28        a   ′           =         N     32        a   ′           N     28        a   ′           =       1     2      cos                 20      °       ≈   0.532               Eq   .              6                                
     Referring again to FIG. 8, in this situation, a flux linkage (or so-called ampere turns) function can be established as: 
     
       
         g(freq)=−0.532i 24n +i 22n −0.532i 26n   Eq. 6 
       
     
     Referring now to Table 1, a chart illustrating the flux linkage for an assumed current value of one is shown at for low frequency harmonics on the power line. The flux linkage g( ) provides a zero impedance to the first (fundamental) frequency, and a non-zero impedance to higher order harmonics, as shown, and thus passes the fundamental frequency while blocking higher order harmonics. Note that, since the core construction provides passage for the triple harmonic fluxes, the harmonic blocking reactor is effective against these harmonics too. 
     
       
         
               
             
               
               
               
               
               
             
               
               
               
               
               
             
           
               
                 TABLE I 
               
             
             
               
                   
               
               
                 Flux linkage for all low harmonics for construction according to Eq. 6 
               
             
          
           
               
                 Harmonics 
                 −0.532 I 24a   
                 I 22a   
                 −0.532 i 26a   
                 g() 
               
               
                   
               
             
          
           
               
                 1 st   
                 −0.532 ∠−20°  
                 1 ∠0° 
                 −0.532 ∠20°  
                 0 
               
               
                 3 rd   
                 −0.532 ∠−60°  
                 1 ∠0° 
                 −0.532 ∠60°  
                 0.4679 
               
               
                 5 th   
                 −0.532 ∠−100° 
                 1 ∠0° 
                 −0.532 ∠100° 
                 1.185 
               
               
                 7 th   
                 −0.532 ∠−140° 
                 1 ∠0° 
                 −0.532 ∠140° 
                 1.8152 
               
               
                 9 th   
                 −0.532 ∠−180° 
                 1 ∠0° 
                 −0.532 ∠180° 
                 2.0642 
               
               
                 11 th    
                 −0.532 ∠140°   
                 1 ∠0° 
                   −0.532 ∠−140° 
                 1.8152 
               
               
                 13 th    
                 −0.532 ∠100°   
                 1 ∠0° 
                   −0.532 ∠−100° 
                 1.185 
               
               
                   
               
             
          
         
       
     
     Table I shows that the impedance produced by the harmonic blocking reactor  14  of FIG. 7 is most effective against the 9 th  harmonic. It is known, however, that in most industrial applications, the 5 th  harmonic is dominant. This inspires us to seek for a construction that may present better impedance to the 5 th  harmonic. 
     Referring now to FIG. 9, a second embodiment of a harmonic blocking reactor  14  constructed in accordance with the present invention is shown. The harmonic blocking reactor  14  of FIG. 9 again comprises three cores  34 ,  36 , and  38 , as well as three winding subsets  28 ,  30 , and  32 . Each winding subset again comprises first, second, and third windings  28   a-c ,  30   a-c , and  32   a-c , respectively, and each of the windings  28   a-c ,  30   a-c , and  32   a-c  comprises a single coil  28   a′-c ′,  30   a′-c ′, and  32   a ′-c′ respectively. 
     In this second embodiment, the first, second, and third ac signals  22   a ,  22   b , and  22   c  are linked to the first, second, and third windings  28   a ,  28   b , and  28   c  of the first winding subset  28 . Similarly, the fourth, fifth, and sixth ac signals  24   a ,  24   b , and  24   c  are linked to the first, second, and third windings  30   a ,  30   b , and  30   c  of the second winding subset  30  and the seventh, eighth, and ninth ac signals  26   a ,  26   b , and  26   c  are linked to the first, second, and third windings  32   a ,  32   b , and  32   c  of the third winding subset  30 . The first winding  28   a  from the winding subset  28 , the second winding  30   b  from the winding subset  30 , and the third winding  32   c  from the third winding subset  32  are each wound around the first core  34 . The second winding  28   b  from the winding subset  28 , the third winding  30   c  from the winding subset  30 , and the first winding  32   a  from the third winding subset  32  are each wound around the second core  36 . The third winding  28   c  from the winding subset  28 , the first winding  30   a  from the winding subset  30 , and the second winding  32   b  from the third winding subset  32  are each wound around the first core  36 . 
     Referring again to FIG. 9, the ac signals coupled to the windings wound about each of the cores  34 ,  36 , and  38  again include one ac signal from the first set of ac signals  22 , one from the second set of ac signals  24 , and one from the third set of ac signals  26 . The ac signals from the second and third set of ac signals are selected to be the second closest signals to the ac signal from the first set of ac signals  22 . For a predetermined angle of twenty degrees, the ac signals coupled to the windings wound about the core  34 , for example, include the signals  22   a  (zero degrees),  24   b  (negative one hundred and forty degrees) and  26   c  (one hundred and forty degrees). The windings wound around the cores  36  and  38  each also comprise three ac signals offset from each other by an angle of one hundred and forty degrees. 
     Again, the harmonic blocking reactor cancels fundamental flux in each of the cores  34 ,  36 , and  38 . Consequently, according to equation 5, and as shown in FIG. 9, the winding turn ratio is:                  N     30        b   ′           N     28        a   ′           =         N     32        a   ′           N     28        a   ′           =       1     2      cos                 140      °       ≈   0.6527               Eq   .              7                                
     Referring again to FIG. 10, in this situation, a flux linkage (or so-called ampere turns) function can be established as: 
     
       
         h(freq)=0.6527i 24b +i 22a +0.6527i 26c   Eq. 8 
       
     
     Table II shows the impedance values at each of the harmonic frequencies. As shown in Table II, zero impedance is applied by the harmonic blocking reactor  14  at the fundamental frequency. The construction of the harmonic blocking reactor  14  of FIG. 9, however, provides a substantial impedance toward the 3 rd , 5 th  and 13 th  harmonics, although the impedance at other harmonic frequencies is lower than that exhibited by the harmonic blocking reactor of FIG.  7 . So generally speaking, the construction of FIG. 7 provides a more substantial impedance to a broad spectra of harmonics, while the construction of FIG. 9 is particularly useful in applications which demonstrate excessive 5 th  harmonics, and minimum other harmonics. 
     
       
         
               
             
               
               
               
               
               
             
               
               
               
               
               
             
           
               
                 TABLE IV 
               
             
             
               
                   
               
               
                 Flux linkage for all low harmonics for construction according to Eq. 8 
               
             
          
           
               
                 Harmonics 
                 0.6527 I 26c   
                 I 22a   
                 0.6527 i 24b   
                 h() 
               
               
                   
               
             
          
           
               
                 1 st   
                 0.6527 ∠40° 
                 1 ∠0° 
                 0.6527 ∠−140° 
                 0 
               
               
                 3 rd   
                 0.6527 ∠60° 
                 1 ∠0° 
                 0.6527 ∠−60°  
                 1.6527 
               
               
                 5 th   
                   0.6527 ∠−20° 
                 1 ∠0° 
                 0.6527 ∠20°   
                 2.227 
               
               
                 7 th   
                    0.6527 ∠−100° 
                 1 ∠0° 
                 0.6527 ∠100°   
                 0.773 
               
               
                 9 th   
                  0.6527 ∠180° 
                 1 ∠0° 
                 0.6527 ∠−180° 
                 −0.3054 
               
               
                 11 th    
                   0.6527 ∠100° 
                 1 ∠0° 
                 0.6527 ∠−100° 
                 0.773 
               
               
                 13 th    
                 0.6527 ∠20° 
                 1 ∠0° 
                 0.6527 ∠−20°  
                 2.227 
               
               
                   
               
             
          
         
       
     
     Referring now to FIG. 11, a third embodiment of the harmonic blocking reactor  14  of the present invention is shown. Here, in order to provide a balanced impedance to all low level harmonics, the harmonic blocking reactor combines the features of the harmonic blocking reactors described with respect to the first (FIG. 7) and second (FIG. 9) embodiments above. 
     The harmonic blocking reactor  14  of FIG. 9 again comprises three cores  34 ,  36 , and  38 , as well as three winding subsets  28 ,  30 , and  32 . Each winding subset again comprises first, second, and third windings  28   a-c ,  30   a-c , and  32   a-c , respectively, and each of the windings  28   a-c ,  30   a-c , and  32   a-c  comprises a first coil  28   a′-c ′,  30   a′-c ′, and  32   a′-c ′, respectively. The second winding subset  30  and third winding subset  32  each also comprise a second coil  30   a″-c ″ and  32   a″-c ″, respectively, wherein each winding  30   a-c  and  32   a-c  comprises a first coil and a second coil coupled in series. 
     In the third embodiment, the first, second, and third ac signals  22   a ,  22   b , and  22   c  are again linked to the first, second, and third windings  28   a ,  28   b , and  28   c  of the first winding subset  28 . Similarly, the fourth, fifth, and sixth ac signals  24   a ,  24   b , and  24   c  are linked to the first, second, and third windings  30   a ,  30   b , and  30   c  of the second winding subset  30  and the seventh, eighth, and ninth ac signals  26   a ,  26   b , and  26   c  are linked to the first, second, and third windings  32   a ,  32   b , and  32   c  of the third winding subset  30 . The first winding  28   a  from the winding subset  28 , the first coil  30   a ′ from first winding  30   a  of the winding subset  30 , the first coil  30   b ′ from the second winding  30   b  of the winding subset  30 , the first coil  32   a ′ from the first winding  32   a  and the first coil  32   c ′ from the third winding  32   c  are each wound around the first core  34 . The second winding  28   b  from the winding subset  28 , the second coil  30   b ″ from second winding  30   b  of the winding subset  30 , the first coil  30   c ′ from the third winding  30   c  of the winding subset  30 , the second coil  32   a ″ from the first winding  32   a  and the first coil  32   b ′ from the second winding  32   b  are each wound around the second core  36 . The third winding  28   c  from the winding subset  28 , the second coil  30   a ″ from first winding  30   a  of the winding subset  30 , the second coil  30   c ″ from the third winding  30   c  of the winding subset  30 , the second coil  32   b ″ from the second winding  32   b  and the second coil  32   c ″ from the third winding  32   c  are each wound around the third core  38 . 
     Referring again to FIG. 11, the ac signals coupled to the windings wound about each of the cores  34 ,  36 , and  38  again include one ac signal from the first set of ac signals  24 , and two signals from the second and third sets of ac signals,  26  and  28  respectively. The ac signals from the second and third set of ac signals are selected to be both the closest and the second closest signals to the ac signal from the first set of ac signals  24 . For a predetermined angle of twenty degrees, the ac signals coupled to the windings wound about the core  34 , for example, include the signals  22   a  (zero degrees),  24   a  (negative twenty degrees),  24   b  (negative one hundred and forty degrees),  26   a  (twenty degrees) and  26   c  (negative one hundred and forty degrees). The windings wound around the cores  36  and  38  are constructed in a similar manner, as can be seen with reference to FIG.  9 . The amp turn ratio of the coils wound about each of the cores  34 ,  36 , and  38  is again selected to cancel fundamental flux in the respective core. For this embodiment, the flux linkage function is calculated as a vector sum of the flux linkages of equations 7 and 8 above, and is constructed as 
     
       
         ƒ(freq)=−0.532i 24a +0.6527 24b +2i 22a −0.532 26a +0.6527 26c   Eq. 9 
       
     
     Table III illustrates the impedance of the flux linkage of the embodiment of FIG. 9 against individual harmonics. Again, the harmonic blocking reactor  14  passes signals at the fundamental frequency while providing an impedance to higher harmonics. 
     
       
         
               
             
               
               
               
               
               
               
               
             
           
               
                 TABLE III 
               
             
             
               
                   
               
               
                 Flux linkage for low frequency harmonics for the harmonic blocking reactor 
               
               
                 of FIG. 9 
               
             
          
           
               
                 Harmonics 
                 −0.532 i1 24a   
                 0.6527 i 24b   
                 I 22a   
                 −0.532 i 26a   
                 0.6527 i 26c   
                 f ( ) 
               
               
                   
               
               
                 1 st   
                 −0.532 ∠20° 
                 0.6527 ∠40° 
                 2 ∠0° 
                 −0.532 ∠20° 
                 0.6527 ∠−140° 
                 0 
               
               
                 3 rd   
                 −0.532 ∠−60° 
                 0.6527 ∠60° 
                 2 ∠0° 
                 −0.532 ∠60° 
                 0.6527 ∠−60° 
                 2.1206 
               
               
                 5 th   
                 −0.532 ∠−100° 
                 0.6527 ∠−20° 
                 2 ∠0° 
                 −0.532 ∠100° 
                 0.6527 ∠20° 
                 3.412 
               
               
                 7 th   
                 −0.532 ∠−140° 
                 0.6527 ∠−100° 
                 2 ∠0° 
                 −0.532 ∠140° 
                 0.6527 ∠100° 
                 2.5882 
               
               
                 9 th   
                 −0.532 ∠−180° 
                 0.6527 ∠180° 
                 2 ∠0° 
                 −0.532 ∠180° 
                 0.6527 ∠−180° 
                 1.7588 
               
               
                 11 th   
                 −0.532 ∠140° 
                 0.6527 ∠100° 
                 2 ∠0° 
                 −0.532 ∠−140° 
                 0.6527 ∠−100° 
                 2.5882 
               
               
                 13 th   
                 −0.532 ∠100° 
                 0.6527 ∠20° 
                 2 ∠0° 
                 −0.532 ∠−100° 
                 0.6527 ∠−20° 
                 3.412 
               
               
                   
               
             
          
         
       
     
     It can be seen with reference to Table III that this configuration passes the fundamental frequency but presents a significant impedance to higher order harmonics. This configuration, therefore, is particularly useful when significant, broad harmonic noise is present. 
     It should be understood that the methods and apparatuses described above are only exemplary and do not limit the scope of the invention, and that various modifications could be made by those skilled in the art that would fall under the scope of the invention. For example, it will be apparent that a harmonic blocking reactor constructed in accordance with the present invention can be configured for use with a number of differently spaced nine phase systems. Furthermore, a harmonic blocking reactor constructed in accordance with the present invention can be used with power converter systems in which the rectifiers are coupled in parallel or series. Additionally, although the harmonic blocking reactor is shown to include a laminated steel core, it will be understood that a number of different known core configurations could be used. It will be apparent that other minor modifications and changes could be made to the configuration without departing from the scope of the invention. It will also be apparent to those of ordinary skill in the art that, although the topologies have been derived from the perspective of AC to DC conversion, the principles of the present invention can also be applied to nine-phase DC to AC system as well. Furthermore, although the examples here illustrate the construction of harmonic blocking reactors using nine-phase currents and three separate continuous flux paths, the principles of the present invention can be easily extended to larger multiphase systems (12, 15, 18, etc.). Nothing in this application is considered critical or essential to the present invention unless explicitly indicated as being critical or essential. 
     To apprise the public of the scope of this invention, the following claims are made: