Abstract:
A motor ( 4 ) comprises a stator which generates a rotating magnetic field according to the energization of plural groups (A, B) of coils, and a rotor rotated by the rotating magnetic field of the stator. An inverter ( 3 ) comprises the same number of switching circuits ( 3 A,  3 B) as the number of groups which supply alternating current to the coils of the groups (A, B) according to the switching action of switching elements (SW 1 -SW 6 , SW 7 -SW 12 ) of each of the switching circuits ( 3 A,  3 B), and a control unit ( 10 ) which controls the switching elements (SW 1 -SW 6 , SW 7 -SW 12 ) so that the sum of the terminal voltages of the coils of each of the groups (A, B) is constant.

Description:
FIELD OF THE INVENTION 
     This invention relates to a combination of an alternating current motor and an inverter which supplies a drive current to the alternating current motor. 
     BACKGROUND OF THE INVENTION 
     An inverter is known which, in order to obtain an alternating current which drives an alternating current motor, changes a direct current into an alternating current of a predetermined frequency and voltage. 
     The direct current is obtained from a battery or by rectifying an alternating current using a converter or a rectifier circuit. 
     SUMMARY OF THE INVENTION 
     In an alternating current motor operated by the output of such an inverter, the voltage of the neutral point of a coil is changed according to switching timings of switching elements of the inverter. This change generates a high frequency leakage current, so if such an alternating current motor is used for driving a vehicle, noise is generated which affects instruments mounted on the vehicle, e.g., the radio. 
     If a noise filter comprising a common mode reactor is inserted in the input circuit and output circuit of the inverter, the high frequency leakage current of the motor may decrease, but a sufficient effect is not necessarily achieved. Moreover, due to the volume and weight of the reactor, the volume and weight of the inverter necessarily increase which makes it unsuitable for installation in a vehicle with limited space. Further, since the reactor is expensive, the cost of the inverter also rises. 
     It is therefore an object of this invention to control the occurrence of the high frequency leakage current in an alternating current motor due to inverter current without using a noise filter. 
     It is another object of this invention to improve the motor efficiency of an alternating current motor which is operated by the output current from an inverter. 
     It is yet another object of this invention to provide a combination of a lightweight, compact inverter without high frequency leakage current, and an alternating current motor. 
     It is yet another object of this invention to suppress the torque ripple of an alternating current motor. 
     In order to achieve the above objects, this invention provides a motor and an inverter which drives the motor, wherein the motor and the inverter have following constructions. 
     The motor comprises a stator and a rotor. The stator comprises plural groups of windings, each of which has coils and generates a rotating magnetic field according to the energization of the coils of each group. The rotor rotates due to the rotating magnetic fields of the plural groups of windings. 
     The inverter comprises an identical number of switching circuits to the number of groups. Each of the circuits comprises plural switching elements and supplying alternating current to the coils of each group according to the switching action of the plural switching elements. The inverter further comprises a control unit which controls the switching elements of the switching circuits corresponding to each group so that the sum of terminal voltages of the coils of each group is constant. 
     This invention also provides a three-phase alternating current motor and an inverter which drives the motor, wherein the motor and the inverter have following constructions. 
     The motor comprises a stator and a motor. The stator generates a rotating magnetic field according to the supply of a three-phase alternating current to a first winding, second winding and third winding corresponding to each phase of the three-phase alternating current. The rotor rotates according to the rotating magnetic field of the stator. 
     The inverter comprises a first switching circuit which supplies alternating current to the first winding according to a switching action of plural switching elements, a second switching circuit which supplies alternating current to the second winding according to a switching action of plural switching elements, and a third switching circuit which supplies alternating current to the third winding according to a switching action of plural switching elements. The inverter further comprises a control unit which controls the switching elements of the first switching circuit, the switching elements of the second switching circuit, and the switching elements of the third switching circuit so that the sum of a terminal voltage of the first winding, a terminal voltage of the second winding and a terminal voltage of the third winding is constant. 
    
    
     The details as well as other features and advantages of this invention are set forth in the remainder of the specification and are shown in the accompanying drawings. 
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIGS. 1A and 1B are a circuit diagram of an inverter and a motor and a schematic diagram of a rotor and a stator according to this invention. 
     FIGS. 2A-2D are tables showing the switching status of switching elements of the inverter driven by a square wave, the current of each coil of a motor, and the neutral point voltage of each coil. 
     FIG. 3 is similar to FIG. 1, but showing the flow of current in the case where the winding direction of the motor differs from that of FIG.  1 . 
     FIGS. 4A-4C are timing charts which show output waveforms from the switching elements of phase U, phase V and phase W when the switching element of the inverter is driven by a square wave. 
     FIGS. 5A-5C are timing charts which show the waveforms of the currents of phase U, phase V and phase W supplied to the motor from the inverter when the switching elements are driven by pulse width modulation (PWM). 
     FIGS. 6A-6C are tables showing the switching status of the switching elements, the current which flows to each coil of the motor and the neutral point voltage when the switching elements are driven by pulse width modulation (PWM). 
     FIGS. 7A-7D are diagrams showing a circuit diagram of the inverter without electrolytic capacitor, the motor, and the current waveforms of various inverter parts. 
     FIG. 8 is a circuit diagram of the inverter and motor housed in the same case. 
     FIG. 9 is a circuit diagram of the inverter and motor according to a second embodiment of this invention. 
     FIG. 10 is a table showing the switching status of the switching elements of the inverter, the current of each coil of a motor, and the neutral point voltage of each coil according to the second embodiment of this invention. 
     FIG. 11 is a circuit diagram of the inverter and motor which housed in the same case according to the second embodiment of this invention. 
     FIG. 12 is a diagram showing an arrangement of a stator winding of the motor according to a third embodiment of this invention. 
     FIG. 13 is a diagram showing the arrangement of the stator winding of FIG. 12 in a different graphic representation. 
     FIG. 14 is similar to FIG. 12 but showing an alternative arrangement of the stator winding. 
     FIG. 15 is similar to FIG. 13 but showing the stator winding of FIG.  14 . 
     FIG. 16 is similar to FIG. 14 but showing another alternative arrangement of the stator winding. 
     FIG. 17 is similar to FIG. 15 but showing the stator winding of FIG.  16 . 
     FIG. 18 is similar to FIG. 16 but showing yet another alternative arrangement of the stator winding. 
     FIG. 19 is a diagram showing an arrangement of the stator winding of the motor according to a fourth embodiment of this invention. 
     FIG. 20 is a diagram showing the arrangement of the stator winding of FIG. 19 in a different graphic representation. 
     FIG. 21 is similar to FIG. 19 but showing an alternative arrangement of the stator winding. 
     FIG. 22 is similar to FIG. 20 but showing the stator winding of FIG.  21 . 
     FIG. 23 is similar to FIG. 21 but showing another alternative arrangement of the stator winding. 
     FIG. 24 is similar to FIG. 22 but showing the stator winding of FIG.  23 . 
    
    
     DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     Referring to FIGS. 1A and 1B, of the drawings, a stator of a three phase alternating current motor  4  comprises a rotor  40  and a stator  41 , and the stator  41  comprises a stator winding A and stator winding B respectively wound in parallel in a phase U, phase V and phase W. 
     A three phase alternating current from a switching circuit  3 A of an inverter  3  is supplied to the stator winding A. A three phase alternating current from a switching circuit  3 B of the inverter  3  is supplied to the stator winding B. 
     The switching circuits  3 A,  3 B of the inverter  3  are connected in parallel to a battery  1 . An electrolytic capacitor  2  to remove ripple current is interposed in a direct current section of the inverter  3  connected directly to the battery  1 . 
     The switching circuit  3 A comprises switching elements SW 1 -SW 6  assembled in a bridge shape. The switching circuit  3 B comprises switching elements SW 7 -SW 12  assembled in a bridge shape. 
     A control unit  10  outputs a signal having a square waveform to the switching elements SW 1 -SW 12  every 60 degrees, as shown in the tables of FIGS. 2A-2C In these figures, ON is expressed as “H” and OFF is expressed as “L.” The switching elements SW 1 -SW 2  perform ON and OFF switching according to this signal. 
     For the phase U, the control unit  10  outputs an identical signal to the switching elements SW 1 , SW 8 . The same signal, but having a phase difference of 180 degrees, is output to the switching elements SW 2  and SW 7 . 
     For the phase W the control unit  10  outputs an identical signal to the switching elements SW 3  and SW 10 . The same signal, but having a phase difference of 180 degrees, is output to the switching elements SW 4  and SW 9 . 
     For the phase V, the control unit  10  outputs an identical signal to the switching elements SW 5  and SW 12 . The same signal, but having a phase difference of 180 degrees, is output for the switching elements SW 6  and SW 11 . 
     As a result of the above signal outputs, currents with a phase difference of 60 degrees with respect to each other are obtained for the phases U, V, W of the stator winding A from the switching circuit  3 A, as shown in FIGS. 4A-4C. 
     Moreover, currents of opposite phase to those of FIGS. 4A-4C flow for the phases U, V, W of the stator winding B from the switching circuit  3 B. 
     That is, the switching performed by the switching circuit  3 A of the inverter  3  which supplies current to the stator winding A of the motor  4 , is opposite to the switching performed by the switching circuit  3 B of the inverter  3  which supplies current to the stator winding B of the motor  4 . 
     If the input voltage from the battery  1  to the inverter  3  is set to Ed, the voltage of the neutral point NA of the phases U, V, W of the stator winding A and stator winding B, will fluctuate between ⅓Ed and ⅔Ed, as shown in FIGS.  2 A and  2 B. 
     Here, the phases of ON and OFF between the switching elements SW 1 -SW 6  and switching elements SW 7 -SW 12  differ by 180 degrees so that, when the switching element SW 1  is ON, the switching element SW 7  is OFF, and when the switching element SW 2  is OFF, the switching element SW 8  is ON. Therefore, the voltage fluctuation of the neutral point NB of the stator winding B is equivalent to a shift of 180 degrees in the phase of the voltage fluctuation of the neutral point NA of the stator winding A. 
     The sum total of the terminal voltages of the motor  4  is the sum of the voltage of the neutral point NA of the stator winding A, and the voltage of the neutral point NB of the stator winding B, and as these voltages have a phase difference of 180 degrees, the sum value of the voltage of the neutral point NA and the voltage of the neutral point NB is always equal to {fraction (3/3)}Ed as shown in FIG.  2 C. Consequently, the sum total of the terminal voltages of the motor  4  is {fraction (3/3)}Ed at any timing, and high frequency current can be stopped from leaking to the direct current side of the inverter  3 . 
     Here, comparing for example the flow directions of the currents in identical phase intervals of FIGS. 2A and 2B, the currents in the stator winding A and stator winding B always flow in opposite directions. 
     If the currents in the stator winding A and stator winding B always flow in opposite directions in this way, the current flow directions of phases U, V, W will all be reversed between the stator winding A and stator winding B. Therefore, if the stator winding A and stator winding B are wound in an identical direction as shown in FIG. 3, as the magnetic fluxes induced by the currents cancel each other out in the stator winding A and stator winding B, the motor  4  cannot be rotated. 
     Therefore, in the stator of this three phase alternating current motor  4 , the winding direction of the stator winding B is arranged to be the reverse of that of the stator winding A, as shown in FIG.  1 A. By reversing the directions of the windings in this way, the direction of the current in the stator winding A is the same as that in the stator winding B as shown in FIG. 2D, even when the switching elements SW 7 -SW 12  perform switching in the same way as that in the table of FIG. 2B, so the motor  4  rotates. 
     On the other hand, as the total terminal voltage of the motor  4  which is the sum of the voltage of the neutral point NA of the stator winding A and the neutral point NB of the stator winding B is kept constant, high frequency current does not leak to the direct current side of the inverter  3 . 
     Instead of the switching elements SW 1 -SW 12  performing switching by a square wave signal, pulse width modulation which is shown in FIGS. 5A-5C can also be used. 
     When switching is performed by pulse width modulation, the change-over frequency of “H” and “L” of the switching elements SW 1 -SW 12  becomes very high, as shown in FIGS. 6A and 6B. 
     However, also in this case, the control principle is the same as that of the first embodiment, and the setting is such that switching between “H” and “L” by the switching elements SW 7 -SW 12 , and switching between “H” and “L” by the switching elements SW 1 -SW 6 , is performed with a phase difference of 180 degrees. In other words, opposite switching is performed in the switching circuits  3 A and  3 B so that, when the switching element SW 1  is “H”, for example, the switching element SW 7  is “L”, and when the switching element SW 2  is “L”, the switching element SW 8  is “H.” 
     Consequently, as shown in FIG. 6C, the total terminal voltage of the motor  4  which is the sum of the voltage of the neutral point NA of coil A and the voltage of the neutral point NB of coil B is {fraction (3/3)}Ed at any timing, and leakage of RF current to the direct current side of the inverter  3  can be suppressed. 
     The electrolytic capacitor  2  for removing ripple current is provided in the direct current section of the inverter  3  in the circuit diagram of FIG. 1A, but the electrolytic capacitor can be omitted for the following reason. 
     The inverter shown in FIG. 7A is the same as the inverter  3  of FIG. 1A, only the electrolytic capacitor having been removed, and the remaining features of the construction are the same as those of the inverter  3  of FIG.  1 A. 
     The phases U, V, W have coils for the stator winding A and for the stator winding B. The switching circuit  3 A supplies alternating current power to the coil of stator winding A, and the switching circuit  3 B supplies alternating current power to the coil of stator winding B. 
     For the coils of the stator windings  3 A,  3 B of identical phase, the switching circuits  3 A,  3 B perform ON/OFF control of the switching elements inversely to each other. As a result, the waveform of the current which flows from the positive electrode of the battery  1  to the switching circuit  3 A, and the waveform of the current which flows from the positive electrode of the battery  1  to the switching circuit  3 B, have opposite phases as shown in FIGS. 7B,  7 C. The waveform of the current which flows to the battery  1  is a combined waveform of these current waveforms, and it is effectively constant as shown in FIG.  7 D. 
     The surge voltage generated when one switching element of the switching circuits  3 A,  3 B is “L” can also be eliminated by the other switching element of the pair is “H.” Consequently, the ripple current can be removed even if the electrolytic capacitor is not provided. This contributes to compactness of the inverter  3 . 
     If the inverter  3  and the motor  4  are built into the same case  11  as shown in FIG. 8, the inverter  3  and motor  4  can be made lightweight and compact which is particularly desirable when they are mounted on a vehicle. 
     Next, a second embodiment of this invention will be described referring to FIGS. 9 and 10. 
     In this embodiment, the stator winding of the motor  4  comprises phase I, phase II and phase III which are mutually independent as shown in FIG.  9 . Switching circuits  3 I,  3 II and  3 III which perform switching are separately connected to the inverter  3 . The switching circuit  3 I is connected to the coil of phase I, the switching circuit  3 II is connected to the coil of phase II, and the switching circuit  3 III is connected to the coil of phase III of the alternating current motor  4 , respectively. 
     The switching circuit  31  comprises a bridge of the switching elements SW 1 -SW 4 , the switching circuit  3 H comprises a bridge of the switching elements SW 5 -SW 8 , and the switching circuit  31 H comprises a bridge of the switching elements SW 9 -SW 12 . 
     By controlling the switching circuits  3 I,  3 II and  3 III by a signal shown in the table of FIG. 10, a current flow is set up so that the sum total of the terminal voltages of the motor  4  does not depend on switching timing, but is always effectively constant as in the first embodiment. 
     For example, in the area where the switching timing is 0 to 60 degrees, by holding the signal to the switching elements SW 1 , SW 4 , SW 5 , SW 8 , SW 9 , SW 12  of the switching circuits  3 I,  3 II and  3 II to “H”, current is passed from the coil of phase I to the coil of phase II and the coil of phase III, as shown by the first pair of solid arrows in the table of FIG.  10 . In the next area of 60 to 120 degrees, the switching elements SW 1 , SW 4 , SW 9 , SW 12  of the switching circuits  3 I,  3 II and  3 II are then held at “H”, the signal to the switching elements SW 5 , SW 8  of the switching circuit  3 II is set to “L”, and the signal to the switching elements SW 6 , SW 7  is set to “H”. This passes a current from the coil of phase I and the coil of phase II to the coil of phase III, as shown by the second pair of solid arrows in the table. Hereafter, the same current flow as in the first embodiment is obtained by outputting “H” and “L” signals to the switching elements alternately every 60 degrees. 
     Consequently, as shown in FIG. 10, the sum of the voltages of the neutral points NI, NII, NIII of phase I, phase II and phase III of the motor  4  are ½Ed compared to the input voltage Ed to the inverter  3 , and the total terminal voltage of the motor does not depend on switching timing but is almost fixed. 
     Also in this embodiment, the electrolytic capacitor may be omitted. 
     Moreover, in this embodiment, by housing the inverter  3  and the motor  4  in the same case  11  as shown in FIG. 11, the inverter  3  and motor  4  can be made more lightweight and compact which is especially suitable for installing in a vehicle. 
     Next, a third embodiment of this invention will be described referring to FIGS. 12-18. 
     This embodiment relates to the winding method of the stator windings A and B of the motor  4 . The circuit layout is identical to that of the first embodiment shown in FIG.  1 A. 
     In this embodiment, concentrated coils are used in the stator windings A and B. 
     It will be assumed that the motor  4  is an eight pole rotor equipped with the same three phase, twelve slot stator as that of FIG.  7 . The stator winding A and stator winding B both comprise coils of phase U, V and W each comprising two slots. For the purpose of identification, the U, V, W phases of the stator winding B will be referred to as U′, V′, W′. 
     The windings in the twelve slots therefore comprise coils arranged in the order U, V, W, U, V, W, U′, V′, W′, U′, V′, W′. The coil windings U, V, W, U, V, W, correspond to the stator winding A, and the coil windings U′, V′, W′, U′, V′, W′correspond to the stator winding B. Due to this coil arrangement, the coil U′ faces the coil U, the coil V′ faces the coil V, and the coil W′ faces the coil W, as shown in FIG.  12 . 
     The winding directions of the coils U, U′ are arranged to be opposite, the winding directions of the coils V, V′ are arranged to be opposite, and the winding directions of the coils W, W′ are arranged to be opposite. 
     Due to this arrangement of concentrated coil windings, the length of the coils can be made shortest in the stator winding A and in the stator winding B. 
     FIGS. 14 and 15 show another arrangement of coils using concentrated coil windings. Herein, the coils are arranged in the order U, V, W, U′, V′, W′, U, V, W, U′, V′, W′. Due to this arrangement of coils, as shown in FIG. 14, the coil U and coil U, coil V and coil V, and coil W and coil W of the stator winding A are respectively arranged at intervals of 180 degrees, and the coil U′ and coil U′, coil V′ and coil V′, and coil W′ and coil W′ of the stator winding B are respectively arranged at intervals of 180 degrees. 
     This arrangement of coils eliminates imbalance of properties between coils of identical phase facing each other, and reduces torque ripple. 
     FIGS. 16 and 17 show yet another arrangement of coils using concentrated coil windings. Herein, the coils are arranged in the order U, V′, W, U′, V, W′, U, V′, W, U′, V, W′. Due to this arrangement also, the coil U and coil U, coil V and coil V, and coil W and coil W of the stator winding A are respectively arranged at intervals of 180 degrees, and the coil U′ and coil U′, coil V′ and coil V′, and coil W′ and coil W′ of the stator winding B are respectively arranged at intervals of 180 degrees. 
     In this arrangement of coils, coils of identical phase are arranged opposite each other, and the coils of the stator winding B are necessarily disposed alongside the coils of the stator winding A. Therefore, imbalance in properties between coils of the same phase can be eliminated, and imbalance of the ends of the coils can also be eliminated, so torque ripple can be reduced further. 
     According to this third embodiment, series windings are used wherein for example after winding the coil of phase U of one slot, a coil of phase U of another slot is wound, however the parallel winding arrangement shown in FIG. 18 may also be adopted depending on electrical design or manufacturing specifications. 
     Next, a fourth embodiment of this invention will be described referring to FIGS. 19-24. 
     This embodiment also relates to the winding method of the stator windings A and B of the motor  4 , and the circuit layout of the inverter  3  and motor  4  is identical to the circuit layout of the first embodiment shown in FIG.  1 A. 
     Whereas in the third embodiment the number of slots was twelve, in this embodiment, the number of slots is twenty four. 
     As shown in FIGS. 19 and 20, in this concentrated arrangement of coils in twenty four slots, the coils are wound in the order U, V, W, U, V, W, U, V, W, U, V, W, U′, V′, W′, U′, V′, W′, U′, V′, W′, U′, V′, W′. In this case also, as in the case of FIG. 12 of the third embodiment, the coil U and coil U′ face each other, the coil V and coil V′ face each other, and the coil W and coil W′ face each other. Also, the coil U and coil U′, coil V and coil V′, and coil W and coil W′ are given opposite winding directions. 
     Further, the coils are wound so that adjacent coils have opposite winding directions. In the above description, one winding direction is represented by U, V, W, U′, V′, W′, and the opposite winding direction is represented by  U ,  V ,  W ,  U′ ,  V′ ,  W′ . This arrangement is possible as there are twenty four slots, i.e., twice the number in the third embodiment. 
     In this winding arrangement, the length of the coils can be made the shortest as in the winding arrangement of FIG. 12 of the third embodiment. 
     FIGS. 21 and 22 show another arrangement of concentrated coil windings in twenty four slots. 
     Herein, the coils are wound in the order U, V, W, U′, V′, W′, U, V, W. U′, V′, W′, U, V, W, U′, V′, W′, U, V, W, U′, V′, W′. The coil U and coil U′, coil V and coil V′ and coil W and coil W′ are respectively wound in the same directions, whereas the coil V is wound in an opposite direction to the coil U and coil W, and the coil V′ is wound in an opposite direction to the coil U′ and coil W′. 
     In other words, in the above representation, the order of coils is U,  V , W, U′,  V′ , W′, U,  V , W, U′,  V′ , W′, U,  V , W, U′,  V′ , W′, U,  V , W, U′,  V′ , W′. 
     In this winding arrangement, all coils having the same phase can be wound in the same direction, so manufacture of the motor  4  is easy. Also, coils of the same phase are arranged at intervals of 180 degrees as in FIG. 14 of the third embodiment, so imbalance of properties between coils of identical phase is eliminated and torque ripple is reduced. 
     FIGS. 23 and 24 show yet another arrangement of concentrated coil windings in twenty four slots. Herein, the order of coils is U, V′, W, U′, V, W′, U, V′, W, U′, V, W′, U, V′, W, U′, V, W′, U, V′, W, U′, V, W′. 
     Due to this arrangement, the winding direction of all coils is the same and the length of coil wire required for the windings is the same for each coil, so manufacture of the motor  4  is easy. Also, as the coils of the stator winding A and the coils of the stator winding B are disposed alternately, imbalances at the ends of the coils are canceled out, and torque ripple is reduced to a very low level. Further, even if one of the switching circuits  3 A,  3 B is faulty, the motor  4  can still be rotated by the other switching circuit. In this case, however, the rotation direction is reversed. 
     The contents of Tokugan Hei 11-134730 and Tokugan Hei 11-134742, both of which have filed on May 14, 1999 in Japan, are hereby incorporated by reference. 
     Although the invention has been described above by reference to certain embodiments of the invention, the invention is not limited to the embodiments described above. Modifications and variations of the embodiments described above will occur to those skilled in the art, in light of the above teachings. 
     The embodiments of this invention in which an exclusive property or privilege is claimed are defined as follows: