Abstract:
An A/D converter system includes a regular A/D converter ( 10 ) with calibration means. Included is also a lower performance, as compared to the regular A/D converter, auxiliary A/D converter ( 20 ). Means ( 22, 24 ) are provided for temporarily switching, at a switching rate that is lower than the sampling rate of regular A/D converter ( 10 ), A/D conversion from the regular A/D converter ( 10 ) to the auxiliary A/D converter ( 20 ) during short time intervals used for calibration of the regular A/D converter ( 10 ).

Description:
TECHNICAL FIELD  
         [0001]    The present invention relates to A/D converters (analog-to-digital converters), and in particular how to enable background calibration of such converters.  
         BACKGROUND  
         [0002]    The maximum achievable accuracy-speed performance of any A/D-converter is limited by non-ideal effects associated with its building blocks. Typically, the performance is limited by settling time, finite amplifier gain and/or analog component mismatch. When designing high-speed, high-accuracy A/D converters, these limitations impose very stringent demands on the building blocks, leading to prolonged design time. They also require the use of manufacturing processes that are optimized for component matching and performance, thus increasing the manufacturing cost.  
           [0003]    Many non-ideal effects can be compensated for by using calibration. The problem is that the efficiency of the calibration may be degraded by drift and ageing. Therefore it is desirable to be able to continuously calibrate the A/D converter during normal operation.  
           [0004]    One of the more popular approaches to background calibration is to use the “skip-and-fill” approach [1]-[2]. During normal operation, every k th  sample is skipped, and the hardware is reconfigured to perform a calibration operation. The gap representing the skipped sample is filled by interpolation by using a number of adjacent samples. The problem with these solutions is that interpolation can only predict the skipped sample accurately when the input signal has a limited bandwidth. If the input signal is completely random, or if it can have any frequency over the entire Nyquist bandwidth, any guess is as good as the interpolated value. In the implementation described in [2], the performance is seen to degrade significantly for input frequencies above ⅔ of the Nyquist frequency (f s /2). So, even with as much as 44 taps interpolation (22 samples before, and 22 samples after the gap), it is not possible to accurately track more than ⅔ of the Nyquist bandwidth. This is in accordance with the theory described in [1]. Such a high-order interpolation requires a significant amount of digital hardware, and a long output delay (latency).  
           [0005]    Another method to create a calibration time-slot is found in [3], where an input sample queue is formed by a cascade of sample-and-hold circuits. By emptying the queue slightly faster than it is filled, a calibration time-slot is occasionally available. The drawback with the “input-queue” method is that each extra sample-and-hold stage adds distortion and noise. Therefore this approach is not optimal for high-speed, high-resolution A/D converters.  
           [0006]    A background calibration approach applicable to pipelined A/D converters is proposed in [4]. The principle is to temporarily remove the pipeline stage to be calibrated from the signal path, and replace it with a substitute extra pipeline stage. Calibration of the disconnected pipeline-stage is then performed outside the pipeline. This “hardware-substitution” method is limited in several ways:  
           [0007]    1. Its application is limited to pipeline A/D converters, or at least to A/D converter architectures having a cascade of identical stages.  
           [0008]    2. The calibration is done outside of the conversion signal path, which means that the stage under calibration is not seeing the same environment as during normal operation. This may lead to incomplete calibration.  
           [0009]    3. The conversion signal path is always filled with conversion samples. Thus it is not possible to insert a calibration value in the pipeline, or switch the pipeline to calibration mode. This effectively rules out the use of a large range of high-performance digital calibration schemes, such as the ones described in [5]-[6].  
           [0010]    Another class of A/D converters is described in [7]. These A/D converters use several identical low sample rate A/D conversion units in parallel to build a high sample rate A/D converter. The units sample the analog signal in a cyclical manner. Calibration of one unit may be performed when another unit is sampling. Thus, no interpolation is necessary. However, this type of parallel converter is also very complex and expensive.  
         SUMMARY  
         [0011]    An object of the present invention is to enable the use of a wide range of calibration methods, without the inherent signal-bandwidth limitations imposed by the interpolation used in prior-art “skip-and-fill” methods and at a lower cost than the parallel A/D converter solution.  
           [0012]    This object is achieved in accordance with the attached claims.  
           [0013]    Briefly, the present invention provides a low performance auxiliary A/D converter that occasionally replaces the regular A/D converter for calibration purposes. Here the term “low performance” means lower performance than the regular A/D converter. The fact that the auxiliary A/D converter only has to be used occasionally (low sampling rate) means that the requirements on the auxiliary A/D converter are lower. Thus, parameters such as bit resolution and settling/conversion time are less critical. 
       
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS  
       [0014]    The invention, together with further objects and advantages thereof, may best be understood by making reference to the following description taken together with the accompanying drawings, in which:  
         [0015]    [0015]FIG. 1 is a block diagram of a conventional A/D converter with an interpolator;  
         [0016]    [0016]FIG. 2 is a time diagram illustrating sampling with the A/D converter of FIG. 1;  
         [0017]    [0017]FIG. 3 is a block diagram of an embodiment of the A/D converter in accordance with the present invention;  
         [0018]    [0018]FIG. 4 is a time diagram illustrating sampling with the A/D converter of FIG. 3;  
         [0019]    [0019]FIG. 5 is a flow chart illustrating the A/D conversion method of the present invention;  
         [0020]    [0020]FIG. 6 is a diagram illustrating performance as a function of resolution of the auxiliary A/D converter for an A/D converter in accordance with the present invention;  
         [0021]    [0021]FIG. 7 is a diagram illustrating performance as a function of skip rate for an A/D converter in accordance with the present invention; and  
         [0022]    [0022]FIG. 8 is another diagram illustrating performance as a function of skip rate for an A/D converter in accordance with the present invention. 
     
    
     DETAILED DESCRIPTION  
       [0023]    [0023]FIG. 1 is a block diagram of a conventional A/D converter with an interpolator.  
         [0024]    An analog signal is forwarded to an A/D converter  10 . The digital samples are forwarded to an interpolator  12  and a delay element  14 . A switch  16  is normally in the indicated upper position, in which the digital samples from delay element  14  are outputted at a sampling interval T. Every k th s ample switch  16  is forced to its lower position, in which a sample is skipped and an interpolated digital sample from interpolator  12  is outputted instead. Thereafter switch  16  returns to its upper position. Calibration, or a part of a complete calibration of A/D converter  10  is performed during the interpolation.  
         [0025]    [0025]FIG. 2 is a time diagram illustrating sampling with the A/D converter of FIG. 1. The dashed line denotes the actual value of the skipped sample. Due to the limited bandwidth of the interpolation, the interpolated value may be different from this actual value. The interpolated value lies on the illustrated interpolation curve that is formed by surrounding samples. These surrounding samples are the reason for delay element  14  in FIG. 1 (in order to be able to interpolate, samples are required both before and after the skipped sample).  
         [0026]    [0026]FIG. 3 is a block diagram of an embodiment of the A/D converter in accordance with the present invention. A normally used regular A/D converter  10  is supplemented by an auxiliary, low performance A/D converter  20 , which is only used occasionally when regular A/D converter  10  is calibrated. Preferably A/D converter  20  is implemented on the same chip as regular A/D converter  10 , but it may also be implemented separately. Switching between the two A/D converters is performed by synchronized switches  22  and  24 . If necessary, two delay elements  26  and  28  with different delays may be provided after A/D converter  10  and  20 , respectively, in order to compensate for a longer settling/conversion time of auxiliary A/D converter  20  and time-align the two data streams.  
         [0027]    [0027]FIG. 4 is a time diagram illustrating sampling with the A/D converter of FIG. 3. It is noted that in this case the actual value of the skipped (by regular A/D converter  10 ) sample is obtained from auxiliary A/D converter  20  (possibly at lower resolution).  
         [0028]    [0028]FIG. 5 is a flow chart illustrating the A/D conversion method of the present invention. Step S 1  determines the next sample position n. Step S 2  tests whether n/k is an integer (m in FIG. 3). Here k denotes the number of samples between calibrations. If n/k is not an integer, step S 3  obtains the next sample with the regular A/D converter. If n/k is an integer, the next sample is obtained by the auxiliary A/D converter in step S 4 , and the regular A/D converter is calibrated in step S 5 . In both cases the procedure thereafter returns to step S 1 .  
         [0029]    It is to be noted that the two A/D converters  10 ,  20  may be of different type.  
         [0030]    Examples of different possible combinations are given in table 1 below.  
                           TABLE 1                                   A/D converter 10   A/D converter 20                           Pipeline   Cyclic           Pipeline   Flash           Pipeline   Successive Approximation           Pipeline   Dual-slope           Pipeline   Pipeline           Flash   Cyclic           Flash   Flash                      
 
         [0031]    These examples are in no way exhaustive. Other combinations are also possible. However, they demonstrate the flexibility offered by the present invention.  
         [0032]    The required resolution N 2  of the auxiliary A/D converter, and how often it is possible to skip-and-fill, depends on the system specifications. A few simulation results are illustrated in FIGS.  6 - 8  as an indication of possible performance.  
         [0033]    [0033]FIG. 6 is a diagram illustrating performance as a function of resolution of the auxiliary A/D converter for an A/D converter in accordance with the present invention. An otherwise ideal 14-bit converter had 10 samples out of 16384 (16K) replaced by an N 2 -bit sample. The SFDR (Spurious Free Dynamic Range) and SINAD (SIgnal-to-Noise-And-Distortion ratio) vs. N 2  are plotted in  20  FIG. 6. It is seen that for N 2  down to 10 bits, the spectral performance shows little or no degradation. For a simple design, it is reasonable to expect N 2  to reach 8 to 10 bits.  
         [0034]    [0034]FIG. 7 is a diagram illustrating performance as a function of skip rate for an A/D converter in accordance with the present invention. FIG. 7 shows how the spectral performance SFDR depends on the skip rate for N 2 ={6, 8, 10} bits. The skip rate is swept from 1 to 10000 skips per 16384 samples, where the latter extreme is almost equivalent to a stand-alone N 2 -bit converter. The simulations indicate that with a 10-bit auxiliary A/D converter, it is possible to skip-and-fill 10 to 30 samples per 16K with only a small degradation in spectral performance. With an 8-bit auxiliary A/D converter, 1 to 3 samples may be skipped, while a 6-bit auxiliary A/D converter has insufficient resolution.  
         [0035]    [0035]FIG. 8 is another diagram illustrating performance as a function of skip rate for an A/D converter in accordance with the present invention. It is similar to FIG. 7, but illustrates how the spectral performance SINAD depends on the skip rate for N 2 ={6, 8, 10} bits.  
         [0036]    From FIGS.  6 - 8  it may be concluded that the performance requirements on the auxiliary A/D converter are much lower than on the regular A/D converter at low skip rates (The skip rate must be lower than half the sampling rate, typically much lower.). This is a very important feature of the present invention.  
         [0037]    A few further embodiments are briefly described below.  
         [0038]    The idle-time of the auxiliary A/D converter can be used for power-down to achieve low-power operation.  
         [0039]    The requirement on settling/conversion time for the auxiliary A/D converter can be greatly relaxed by increasing the delay after the regular A/D converter.  
         [0040]    The auxiliary A/D converter can use dynamic element matching to ensure that, while possibly having lower resolution, it does not have excessive non-linearity.  
         [0041]    Allowing the auxiliary A/D converter to fill two or more consecutive samples, enables the use of background calibration schemes needing two or more consecutive samples for proper function. It is also possible to use two or more auxiliary A/D converters in parallel to fill two or more consecutive samples.  
         [0042]    It is possible to use a dedicated sample-and-hold circuit for the auxiliary A/D converter, so that it can be fed with an input sample during a prolonged time. This can be useful for example when the auxiliary A/D converter is of successive approximation type.  
         [0043]    In another embodiment of the invention the regular A/D converter may be interrupted at randomly instead of periodically selected sampling instants.  
         [0044]    An important advantage of the present invention is that the auxiliary A/D converter converts the actual signal, as opposed to calculating an interpolated value from neighboring samples. Therefore, no pre-knowledge of the signal is needed, and the “fill” value inserted in accordance with the present invention, is accurately predicted even if the full Nyquist bandwidth is used for input signals.  
         [0045]    Furthermore, the present invention represents a generic method, applicable to background calibration of most known wideband A/D converter architectures, and therefore covers a large number of applications, for example applications related to digital radio systems.  
         [0046]    A further advantage is that the present invention is not limited to a particular calibration scheme. Instead, by using the present invention it becomes possible to choose from a wide range of existing background calibration schemes—schemes previously excluded due to the inherent bandwidth—limitations of interpolation-type skip-and-fill methods.  
         [0047]    It will be understood by those skilled in the art that various modifications and changes may be made to the present invention without departure from the scope thereof, which is defined by the appended claims.