Abstract:
Disclosed is a predistorter for preliminarily compensating a distortion caused in a circuit comprising a modulator, a variable gain amplifier, and a non-linear amplifier, the predistorter comprising: an amplitude detector for detecting an amplitude of an input signal; a gain detector for detecting a gain of the variable gain amplifier; a first multiplier for multiplying the amplitude of the input signal with the gain of the variable gain to output a product therebetween; a generator for generating a predistortion function corresponding to the product; and a second multiplier for multiplying the input signal with the predistortion function to output a product therebetween to the modulator.

Description:
BACKGROUND OF THE INVENTION 
     1. Field of the Invention 
     The present invention relates to a predistorter and particularly, to the predistorter which has a variable gain circuit for power control. 
     2. Description of the Prior Art 
     A predistorter is conventionally used for the purpose of preliminarily compensating, at a baseband, a distortion caused in a transmission power amplifier of a radio communication apparatus, and thereby reducing a spurious radiation caused by a non-linearity of the transmission power amplifier. In the case where a predistorter is used in the radio communication apparatus, a transmission power amplifier can operate in a non-linear region and accordingly, the power consumption during transmission of the radio communication apparatus can be decreased. If the radio communication apparatus is a portable phone which uses a battery as its power source in such a case, a talk time can be elongated. 
     Predistorters as explained above have been developed actively heretofore. The theory and structure of a predistorter is explained in detail in “Quantization Analysis and Design of a Digital Predistortion Linearizer for RF Power Amplifier”, Sundstrom L., Faulkner M., Johansen M.; Vehicular Technology, IEEE Trans. Vol. 45 4, pages 707-719. 
     A conventional predistorter will be explained hereunder while making reference to the above article. 
     In conventional mobile communications, it has been adopted a constant envelope modulation system such as FM system and GMSK system, in which an amplitude of a modulated signal is constant and information is carried on phase variation of the modulated signal. The reason for the adoption is that the constant amplitude enables the use of a C- or F-class non-linear amplifier which has a high power efficiency as a transmission power amplifier. In the case where a transmission power amplifier with a high power efficiency is used, the power consumption during a transmission is reduced and, if a portable phone is used, a talk time can be elongated. 
     Heretofore, however, increase in traffic has become a problem in mobile communication. 
     Hence, a modulation system with a high efficiency in frequency use also has been used. For example, PDC (personal Digital Cellular) and PHS (Personal Handyphone System) in Japan adopt π/4 shift QPSK. In addition, CDMA (Code Division Multiple Access) system adopts QPSK or offset QPSK. 
     These modulation systems are referred to as linear modulation systems, in which information is carried on amplitude as well as on phase. In such systems, a non-linear amplifier can not be adopted because the amplitude of a modulated signal varies within wide range. That is, it is needed to adopt an amplifier with a linearity as precise as possible. 
     FIG. 3 shows an example of an output spectrum in the case here an amplifier with a poor linearity is used. 
     A bold line in FIG. 3 represents an original spectrum in a linear modulation system. In the case where a modulated signal passes through an amplifier with a poor linearity, spurious signals with a bandwidth, for example, three times as wide as the original signal (or third order distortion components) represented by a broken line are generated because of the influence of the third order distortion of the amplifier. 
     In such case where the spurious signals are generated, ACPR (Adjacent Channel Power Ratio) becomes worse and accordingly, efficiency in frequency use is lowered in spite of adoption of a linear modulation system with high efficiency in frequency use. This phenomenon is referred to as Spectrum Re-generation. 
     In order to avoid this phenomenon, it is necessary to cause an amplifier to operate in a region where it&#39;s linearity is sufficiently precise. 
     However, the better the linearity of an amplifier is, the more the amplifier consumes a power and the lower the power efficiency thereof becomes. 
     Linealizers such as predistorter have been developed as means for alleviating such problem. That is, a countermeasure to this problem is to use an amplifier with high power efficiency and poor linearity and a predistorter for compensating the poor linearity, thereby suppressing spurious powers to adjacent channels. 
     FIG. 4 shows an example of a distortion of a transmission power amplifier. 
     As shown in FIG. 4, as an input level increases, a gain gradually decreases and input-output characteristics gradually deviate from a straight line and eventually saturate. In addition, phase characteristics deviate from a certain constant from a point close to where the input-output characteristics begin to deviate from the straight line. 
     An input signal is a complex number which has an amplitude and an angle (or phase) and represented as: 
     
       
           S   r =( I   r   +jQ   r )exp( j 2 πf   c   t ), 
       
     
     where 
     I r : an in-phase component of a baseband signal 
     Q r : a quadrature component of the baseband signal 
     f c : carrier frequency. 
     Here, in the case where S r  is regarded as representing a baseband signal, the exponential part is omitted and the baseband signal is represented as: 
     
       
         
           S 
           r 
           =I 
           r 
           +jQ 
           r 
         
       
     
     In the case where the signal S r  is inputted to an amplifier, the output level becomes |S o |′ because of the distortion, though the output level should be |S o | originally. In addition, the phase shifts by θ 1 . This relation generates the Spectrum Re-generation, which deteriorates ACPR. 
     A predistorter is effective to avoid the above. In order to cause the amplifier to output the output level S o , it is necessary to supply to the amplifier the input S p  which has been preliminarily calculated instead of the input S r . 
     FIG. 5 shows a complex plane for explaining the compensation of a distortion carried out by the predistorter. 
     As shown in FIG. 5, the predistorter needs to generate the signal S p  which has an amplitude made higher than that of signal S r  in consideration of the saturation of the characteristics of the amplifier and has a phase θ 2  in a direction for canceling the phase rotation. 
     FIG. 6 is a diagram for explaining the formulation of the compensation of the distortion as shown in FIG.  5 . 
     In FIG. 6, G represents the input-output characteristics of the amplifier and F represents the input-output characteristics of a predistorter. Both G and F include phase and are represented with complex numbers. 
     It is obvious from FIG. 6 that the signal S p  which has been predistorted is represented as: 
     
       
           S   p   =F (| S   r |)· S   r   
       
     
     It is obvious that F is determined by only the amplitude of S r  or the absolute value of S r . The output S o  of the amplifier is represented as: 
     
       
           S   o   =G (| S   p |)· S   p   =G{|F (| S   r |)· S   r   |}·F (|S r |)· S   r   
       
     
     In order to establish a linear relationship between S o  and S r , it is necessary to satisfy the following equation: 
     
       
           G{|F (| S   r |)· S   r   |}·F (| S   r |)= C =constant 
       
     
     If an objective value of C, the characteristics G of the amplifier, and the input signal S r  are determined, then the predistortion function F is determined by using the above equation. Here, the function F is represented with a complex number or with a real part Re and an imaginary part Im. 
     FIG. 7 shows the structure of an example of general adaptive predistorters. Here, an input signal (or a source signal) can be treated as a complex signal which has, in a real part, an in-phase component I r  with respect to a carrier and, in an imaginary part, a quadrature component Q r  with respect to the carrier. 
     This conventional predistorter comprises: look-up table  23  in which a real part Re and imaginary part Im of a predistortion function is stored and which outputs the function value F in response to the amplitude of the input signal used as an address thereof; complex multiplier  20  which multiplies the function value F with the input signal by complex multiplication; digital-to-analog converter  21  which converts the result of the multiplication in the complex multiplier  20  to an analog signal and outputs the analog signal; quadrature modulator  22  which modulates the analog signal supplied from digital-to-analog converter  21  by quadrature modulation and outputs a modulated signal as an RF (radio frequency) signal; non-linear amplifier  11  which amplifies the radio frequency signal and outputs an amplified RF signal; coupler  12  which shunts the amplified RF signal into two RF signals; antenna  13  which transmits one of the signals shunted by coupler  12  as a radio wave; quadrature demodulator  26  which demodulates the other of the signals shunted by coupler  12  by quadrature demodulation and outputs a demodulated signal as a complex baseband signal; analog-to-digital converter  25  which converts the baseband signal to a digital signal and output the digital signal; and adaptation circuit  24  which compares the digital signal outputted from analog-to-digital converter  25  with the input signal and updates look-up table  23  in accordance with the result of the comparison. 
     In the predistorter having the structure as explained above, the structure of adaptation circuit  24  becomes complicated because adaptation circuit  24  needs to have a function of comparing the demodulated signal and the input signal while adjusting the timing and phase therebetween. In addition, a transmission level from antenna  13  must be determined in accordance with the input signal. 
     On the other hand, it is necessary to vary transmission power within a range as wide as 80 dB in CDMA system in order to solve the near-far effect. 
     FIG. 8 shows the structure of another example of general adaptive predistorters. 
     Referring to FIG. 8, this conventional predistorter comprises: amplitude calculation circuit  15  which calculates an amplitude of an input signal using components I r  and Q r  of the input signal, ROM  14  in which a real part Re and imaginary part Im of a predistortion function are stored and which outputs the function value F in response to the amplitude of the input signal calculated in amplitude calculation circuit  15  and used as an address thereof; complex multiplier  20  which consists of four multipliers  1  through  4  and two adders  5  and  6  and multiplies the function F and the input signal by complex multiplication; digital-to-analog converters  7  and  8  which convert the results of the multiplication in complex multiplier  20  to analog signals and output the analog signals; quadrature modulator  9  which modulates the analog signals outputted from digital-to-analog converters  7  and  8  by quadrature modulation and outputs a modulated signal as an RF signal; variable gain amplifier  10  which amplifies the RF signal outputted from quadrature modulator  9  with a gain corresponding to a gain control signal supplied from the external and outputs the amplified RF signal; non-linear amplifier  11  which amplifies the RF signal outputted from variable gain amplifier  10  and outputs the RF signal amplified therein; and antenna  13  which transmits the RF signal outputted from non-linear amplifier  11  as a radio wave. 
     In the predistorter having the structure as explained above, the amplitude of the input signal is calculated in amplitude calculation circuit  15  using input components I r  and Q r , the value of function F is outputted from ROM  14  using the result of the calculation as an address, and the value of function F thus outputted and the input signal consisting of components I r  and Q r  are multiplied each other by complex multiplier  20 . 
     Here, a transmission level from antenna  13  is determined not only by the input signal consisting of components I r  and Q r  but also by the gain control signal G c  inputted to variable gain amplifier  10 , because variable gain amplifier  10  is inserted between quadrature modulator  9  and non-linear amplifier  11 . 
     In the latter conventional predistorter, there is a disadvantage that it is impossible to compensate a distortion accurately when the gain control signal varies because a transmission level from antenna  13  is determined by an amplitude of the input signal and a gain of variable gain amplifier  10  and the gain of variable gain amplifier  10  varies when the gain control signal varies. 
     Even if adaptation circuit  24  is introduced to the latter conventional predistorter, it is extremely difficult to stably perform adaptation operation because a predistortion is necessary only in a short period while a gain of variable gain amplifier  10  is high. 
     SUMMARY OF THE INVENTION 
     In order to overcome the aforementioned disadvantages, the present invention has been made and accordingly, has an object to provide a predistorter which correctly compensates a distortion of a non-linear amplifier even when a gain of a variable gain amplifier varies. 
     According to a first aspect of the present invention, there is provided a predistorter for preliminarily compensating a distortion caused in a circuit comprising a modulator, a variable gain amplifier, and a non-linear amplifier, the predistorter comprising: an amplitude detector for detecting an amplitude of an input signal; a gain detector for detecting a gain of the variable gain amplifier; a first multiplier for multiplying the amplitude of the input signal with the gain of the variable gain to output a product therebetween; a generator for generating a predistortion function corresponding to the product; and a second multiplier for multiplying the input signal with the predistortion function to output a product therebetween to the modulator. 
     According to a second aspect of the present invention, there is provided a method for preliminarily compensating a distortion caused in a circuit comprising a modulator, a variable gain amplifier, and a non-linear amplifier, the method comprising steps of: detecting an amplitude of an input signal; detecting a gain of the variable gain amplifier; multiplying the amplitude of the input signal with the gain of the variable gain to output a product therebetween; generating a predistortion function corresponding to the product; and multiplying the input signal with the predistortion function to output a product therebetween to the modulator. 
     According to a third aspect of the present invention, there is provided a transmitter comprising: the predistorter of the first aspect; a modulator for modulating an output of the predistorter; a variable gain amplifier for amplifying an output of the modulator; a non-linear amplifier for amplifying an output of the variable gain amplifier; and an antenna for transmitting an output of the non-linear amplifier as a radio wave. 
     According to a fourth aspect of the present invention, there is provided a radio communication apparatus comprising the transmitter of the third aspect. 
     These and other objects, features and advantages of the present invention will become more apparent in light of the following detailed description of the best mode embodiments thereof, as illustrated in the accompanying drawings. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is a block diagram showing a first embodiment of a predistorter according to the present invention; 
     FIG. 2 is a block diagram showing a second embodiment of a predistorter according to the present invention; 
     FIG. 3 is a spectrum diagram showing an example of an output spectrum in the case where an amplifier with a poor linearity is used; 
     FIG. 4 is a diagram showing an example of a distortion of a transmission power amplifier; 
     FIG. 5 is a complex plane for explaining the compensation of a distortion carried out by a predistorter; 
     FIG. 6 is a block diagram for explaining the formulation of the compensation of the distortion as shown in FIG. 5; 
     FIG. 7 is a block diagram showing a first conventional predistorter; and 
     FIG. 8 is a block diagram showing a second conventional predistorter. 
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     Preferred embodiments according to the present invention will be explained with reference to the accompanying drawings. 
     [First Embodiment] 
     As shown in FIG. 1, this embodiment comprises: amplitude calculation circuit  15  which calculates an amplitude of an input signal S r  using a baseband signal I r  which is an in-phase component of the input signal S r  with respect to a transmission carrier and a baseband signal Q r  which is a quadrature component of the input signal S r  with respect to the transmission carrier; ROM  14  in which a real part Re and imaginary part Im of a predistortion function are stored and which outputs a prescribed distortion-compensating data; complex multiplier  20  which comprises four multipliers  1  through  4  and two adders  5  and  6  and which multiplies a distortion-compensating data outputted from ROM  14  with the input signal S r  by complex multiplication; digital-to-analog converters  7  and  8 , which convert a result of multiplication in complex multiplier  20  to analog signals and output the analog signals; quadrature modulator  9  which modulates the analog signals outputted from digital-to-analog converters  7  and  8  by quadrature modulation and outputs a modulated signal as an RF signal; variable gain amplifier  10  which amplifies the RF signal outputted from quadrature modulator  9  with a gain corresponding to a gain control signal supplied from the external and outputs the amplified RF signal; non-linear amplifier  11  which amplifies the amplified RF signal outputted from variable gain amplifier  10  and outputs an RF signal amplified therein; antenna  13  which transmits the RF signal outputted from non-linear amplifier  11  as a radio wave; gain calculation circuit  16  which inputs the gain control signal also inputted to variable gain amplifier  10  and which calculates the gain of variable gain amplifier  10  on the basis of the gain control signal; and multiplier  30  which multiplies the amplitude calculated in amplitude calculation circuit  15  with the gain calculated in gain calculation circuit  16 . ROM  14  outputs the distortion-compensating data in response to the result of multiplication in multiplier  30  which is used an address thereof. Here, the input signal S r  is a complex number consisting of a real part I r  and an imaginary part Q r . 
     An operation of the predistorter having the structure as explained above will be explained hereunder. 
     Amplitude calculation circuit  15  calculates an instantaneous amplitude |S r | of the input signal S r  when the input signal Sr is (or the real part I r  and the imaginary part Q r  are) supplied to amplitude calculation circuit  15 . |S r | is calculated by using the following equation: 
     
       
         | S   r |=( I   r   2   +Q   r   2 ) ½   
       
     
     In addition, gain calculation circuit  16  calculates an actual value A of the gain of variable gain amplifier  10  on the basis of a value of the gain control signal G c  supplied from the external. 
     Multiplier  30  multiplies the instantaneous amplitude of the input signal S r  calculated in amplitude calculation circuit  15  with the value A of the gain of variable gain amplifier  10  calculated in gain calculation circuit  16 . The result X of the multiplication is used as an address of ROM  14 . Here, address X of ROM  14  is given by the following equation and is proportional to an instantaneous amplitude of a transmission power. 
       X=A·|S   r   |=A ·( I   r   2   +Q   r   2 ) ½   
     Then, ROM  14  outputs the distortion-compensating data, the real part of which is Re and the imaginary part of which is Im, in response to address X. 
     Thereafter, complex multiplier  20  multiplies the input signal S r  and the distortion-compensating data outputted from ROM  14  by complex multiplication. 
     Here, the result of multiplication in complex multiplier  20  is a complex number signal S p  which is the input signal S r  compensated in amplitude and phase so that a non-linearity of non-linear amplifier  11  is canceled. As a result of the multiplication, the signal S p  becomes as follows: 
     
       
           S   p =( Re+jIm )· S   r =( Re+jIm )·( I   r   +jQ   r )=( Re·I   r   −Im·Q   r )+ j ( Re·Q   r   +Im·I   r ) 
       
     
     Here, the real part Re and the imaginary part Im are written as: 
     Re=α·cos θ 
     Im=α·sin θ 
     α: amplitude compensation factor 
     θ: phase compensation factor 
     Substituting the above equation pair to the equation of S p , the S p  is rewritten as: 
     
       
           S   p   =S   r ·α·exp( j θ) 
       
     
     The above equation means that the compensated signal S p  is obtained by multiplying the input signal S r  with α in amplitude and rotating the input signal S r  by θ in phase. 
     The real part I p  and imaginary part Q p  of the compensated signal S p  are written as follows: 
     
       
         
           I 
           p 
           =Re·I 
           r 
           −Im·Q 
           r 
         
       
     
     
       
         
           Q 
           p 
           =Re·Q 
           r 
           +Im·I 
           r 
         
       
     
     The real part I p  and the imaginary part Q p  are converted to analog signals in digital-to-analog converters  7  and  8 , and converted to an RF signal in quadrature modulator  9 . 
     In CDMA system, a precise transmission power control is necessary in order to solve the near-far effect. Therefore, variable gain amplifier  10  is inserted between quadrature modulator  9  and non-linear amplifier  11  to precisely control transmission power. 
     The RF signal outputted from quadrature modulator  9  is amplified in variable gain amplifier  10  and the gain of variable gain amplifier  10  is controlled by the gain control signal Gc. It is usual that the gain control signal Gc has a voltage or control value which corresponds to, for example, is proportional to, a dB value of the gain of variable gain amplifier  10 . 
     Thereafter, the signal amplified in variable gain amplifier  10  is also amplified in non-linear amplifier  11  and transmitted via antenna  13 . 
     Here, both an amplitude distortion and phase distortion generated in non-linear amplifier  11  are determined by an amplitude of an input signal to non-linear amplifier  11 . Therefore, if address X of ROM  14  is determined, then the distortion are also determined. That is, distortion compensation data Re and Im for compensation the distortions are uniquely determined. 
     Therefore, it is appropriate to measure the distortion of non-linear amplifier  11  in the case where address of ROM  14  is X and write the distortion-compensating data Re and Im which is obtained on the basis of the the distortion to ROM  14  as a data in the address X in advance. 
     As explained above, according to this embodiment, it is possible to perform a proper compensation for a distortion even when a gain of variable gain amplifier  10  varies, because a product of a gain of variable gain amplifier  10  and an amplitude of the input signal Sr, which product is proportional to an instantaneous level of an input signal of non-linear amplifier  11 , is used as an address of ROM  14  which outputs a distortion-compensating data. 
     [Second Embodiment] 
     The second embodiment employs another method for compensating a gain variation of variable gain amplifier  10 . 
     As shown in FIG. 2, this embodiment comprises: amplitude calculation circuit  15  which calculates an amplifier of an input signal S r  using a baseband signal I r  which is an in-phase component of the input signal S r  with respect to a transmission carrier and a baseband signal Q r  which is a quadrature component of the input signal S r  with respect to the transmission carrier; ROM  14  in which a real part Re and imaginary part Im of a predistortion function are stored and which outputs a prescribed distortion-compensating data; complex multiplier  20  which comprises four multipliers  1  through  4  and two adders  5  and  6  and which multiplies a distortion-compensating data outputted from ROM  14  with the input signal S r  by complex multiplication; digital-to-analog converters  7  and  8  which convert a result of multiplication in complex multiplier  20  to analog signals and output the analog signals; quadrature modulator  9  which modulates the analog signals outputted from digital-to-analog converters  7  and  8  by quadrature modulation and outputs a modulated signal as an RF signal; variable gain amplifier  10  which amplifiers the RF signal outputted from quadrature modulator  9  with a gain corresponding to a gain control signal supplied from the external and outputs the amplified RF signal; non-linear amplifier  11  which amplifies the amplified RF signal outputted from variable gain amplifier  10  and outputs an RF signal amplified therein; coupler  12  which shunts the amplified RF signal outputted from non-linear amplifier  11  into two RF signals; antenna  13  which transmits one of the signals shunted by coupler  12  as a radio wave; wave detector  19  which detects the other of the signals shunted by coupler  12 ; low pass filter  18  which filters a voltage obtained by wave detector  19  with a cut-off frequency sufficiently low to eliminate an instantaneous amplitude variation but allowing the frequency of transmission power control to pass therethrough; analog-to-digital converter  17  which converts a signal which passed low pass filter  18  to a digital signal and outputs the digital signal; gain calculation circuit  16  which calculates the gain of variable gain amplifier  10  on the basis of the digital signal outputted from analog-to-digital converter  17 ; and multiplier  30  which multiplies the amplitude calculated in amplitude calculation circuit  15  with the gain calculated in gain calculation circuit  16 . ROM  14  outputs the distortion-compensating data in response to the result of multiplication in multiplier  30  which is used as an address thereof. 
     In the predistorter having the structure as explained above, the signal outputted from non-linear amplifier  11  is shunted into two signals by coupler  12 , and one of the two signals is inputted to and detected by wave detector  19 . 
     In low pass filter  18 , the voltage obtained in wave detector  19  is filtered with the above mentioned cut-off frequency. The voltage thus obtained is approximately proportional to the average output amplitude of non-linear amplifier  11 . 
     The signal which passed through low pass filter  18  is converted to the digital signal by analog-to-digital converter  17 , and thereafter, a gain compensation value A is calculated in gain calculation circuit  16 . 
     Unlike the first embodiment, in the second embodiment, it is needless to execute conversion from a dB value to an actual value in connection with the gain of variable gain amplifier  10 , because the output of analog-to-digital converter  17  is approximately proportional to the average output amplitude of non-linear amplifier  11 . 
     Thereafter, multiplier  16  multiplies the value of A calculated in gain calculation circuit  16  with an instantaneous amplitude |S r | of the input signal S r  in order to obtain a product equivalent to address X of the first embodiment. The product is also proportional to an instantaneous amplitude of the transmission power. 
     In the case where a gain of variable gain amplifier  10  or any other circuit varies in conjunction with variation in ambient temperature, it is difficult for the first embodiment to accurately compensate the non-linearity of non-linear amplifier  11 , whereas, in such a case, it is easy for the second embodiment to accurately compensate the non-linearity of non-linear amplifier  11  as long as wave detector  19 , low pass filter  18 , and analog-to-digital converter  17  stably operate, because it is possible to eliminate the influence of variation in ambient temperature. In actual, it is much easier to manufacture stable wave detector  19 , low pass filter  18 , and analog-to-digital converter  17  as compared with to manufacture stable variable gain amplifier  10 . 
     As explained above, according to the present invention, it is possible to properly compensate a non-linearity of a non-linear amplifier even when a gain of a variable gain amplifier varies, because adopted is such structure in which a gain of the variable gain amplifier is obtained, the gain is multiplied with an amplitude of an input signal to obtain a pruduct which is proportional to an instantaneous input level of the non-linear amplifier, a value of a predistortion function is obtained in accordance with the product, and the input signal is predistorted with the value of the predistortion function. 
     Although the present invention has been shown and explained with respect to the best mode embodiments thereof, it should be understood by those skilled in the art that the foregoing and various other changes, omissions, and additions in the form and detail thereof may be made therein without departing from the spirit and scope of the present invention.