Abstract:
An antenna arrangement comprises a patch conductor ( 102 ) having a feed conductor ( 106 ) connected to a first point and a grounding conductor ( 108 ) connected between a second point and a ground plane ( 104 ). An example of such an arrangement is a conventional planar inverted-F antenna. A problem with such antennas is that their impedance is inductive, making them difficult to feed. The present invention incorporates a slot ( 702 ) in the patch conductor ( 102 ) between the first and second points, which enables the inductive component of the antenna&#39;s impedance to be substantially reduced. Suitable positioning of the slot ( 702 ) on the patch conductor ( 102 ) also enables an impedance transformation to be achieved. The antenna described above may have a substantially reduced volume compared with known planar antennas with minimal reduction in performance.

Description:
FIELD OF THE INVENTION 
     The present invention relates to an antenna arrangement comprising a substantially planar patch conductor, feeding means connected to the conductor at a first point and grounding means connected to the conductor at a second point, and to a radio communications apparatus incorporating such an arrangement. 
     BACKGROUND OF THE INVENTION 
     Wireless terminals, such as mobile phone handsets, typically incorporate either an external antenna, such as a normal mode helix or meander line antenna, or an internal antenna, such as a Planar Inverted-F Antenna (PIFA) or similar. 
     Such antennas are small (relative to a wavelength) and therefore, owing to the fundamental limits of small antennas, narrowband. However, cellular radio communication systems typically have a fractional bandwidth of 10% or more. To achieve such a bandwidth from a PIFA for example requires a considerable volume, there being a direct relationship between the bandwidth of a patch antenna and its volume, but such a volume is not readily available with the current trends towards small handsets. Further, PIFAs become reactive at resonance as the patch height is increased, which is necessary to improve bandwidth. 
     SUMMARY OF THE INVENTION 
     An object of the present invention is to provide a planar antenna arrangement requiring a substantially smaller volume than known PIFAs and having improved impedance characteristics while providing similar performance. 
     According to a first aspect of the present invention there is provided an antenna arrangement comprising a substantially planar patch conductor, a feed conductor connected to the patch conductor at a first point and grounding conductor connected between a second point on the patch conductor and a ground plane, wherein the patch conductor incorporates a slot between the first and second points. 
     The presence of a slot affects the differential mode impedance of the antenna arrangement by increasing the length of the short circuit transmission line formed by the feeding and grounding means, thereby enabling the inductive component of the impedance of the arrangement to be significantly reduced. By a suitable asymmetric arrangement of the slot on the patch conductor, an impedance transformation can be achieved. This would typically be used to increase or decrease the resistive impedance of the arrangement for better matching to a 50 Ω circuit. 
     An antenna arrangement made in accordance with the present invention can have a substantially reduced separation between patch conductor and ground plane compared with known patch antennas. This enables a significant volume reduction, thereby enabling improved designs of mobile phone handsets and the like. 
     An antenna arrangement made in accordance with the present invention is also suited for being fed via broadbanding circuitry, for example a shunt LC resonant circuit. 
     According to a second aspect of the present invention there is provided a radio communications apparatus including an antenna arrangement made in accordance with the present invention. 
     The present invention is based upon the recognition, not present in the prior art, that the provision of a slot between feed and grounding pins in a PIFA can substantially reduce the inductive impedance of the antenna. 
     By means of the present invention PIFAs having improved performance and reduced volume are enabled. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     Embodiments of the present invention will now be described, by way of example, with reference to the accompanying drawings, wherein: 
     FIG. 1 is a perspective view of a PIFA mounted on a handset; 
     FIG. 2 is a graph of simulated return loss S 11  in dB against frequency f in MHz for the PIFA of FIG. 1; 
     FIG. 3 is a Smith chart showing the simulated impedance of the PIFA of FIG. 1 over the frequency range 1000 to 3000 MHz; 
     FIG. 4 shows a model of a PIFA as a top-loaded folded monopole formed from a combination of common mode and differential mode circuits; 
     FIG. 5 is a graph of return loss S 11  in dB against frequency f in MHz for the PIFA of FIG. 2 simulated as a summation (solid line) of common mode (dashed line) and differential mode (dotted line) circuits; 
     FIG. 6 is a Smith chart showing the impedance of the PIFA of FIG. 2 simulated as a summation (solid line) of common mode (dashed line) and differential mode (dotted line) circuits; 
     FIG. 7 is a perspective view of a slotted PIFA mounted on a handset; 
     FIG. 8 is a graph of simulated return loss S 11  in dB against frequency f in MHz for the slotted PIFA of FIG. 7; 
     FIG. 9 is a Smith chart showing the simulated impedance of the slotted PIFA of FIG. 7 over the frequency range 1000 to 3000 MHz; 
     FIG. 10 is a graph of return loss S 11  in dB against frequency f in MHz for the slotted PIFA of FIG. 7 simulated as a summation (solid line) of common mode (dashed line) and differential mode (dotted line) circuits; 
     FIG. 11 is a Smith chart showing the impedance of the slotted PIFA of FIG. 7 simulated as a summation (solid line) of common mode (dashed line) and differential mode (dotted line) circuits; 
     FIG. 12 is a perspective view of a slotted PIFA having reduced height mounted on a handset; 
     FIG. 13 is a graph of simulated return loss S 11  in dB against frequency f in MHz for the slotted PIFA of FIG. 12; 
     FIG. 14 is a Smith chart showing the simulated impedance of the slotted PIFA of FIG. 12 over the frequency range 2000 to 2800 MHz; 
     FIG. 15 is a plan view of a slotted PIFA suitable for a Bluetooth application; 
     FIG. 16 is a graph of simulated return loss S 11  in dB against frequency f in MHz for the slotted PIFA of FIG. 15 with no matching network; 
     FIG. 17 is a Smith chart showing the simulated impedance of the slotted PIFA of FIG. 15 with no matching network over the frequency range 2000 to 2900 MHz; 
     FIG. 18 is a graph of simulated return loss S 11  in dB against frequency f in MHz for the slotted PIFA of FIG. 15 with a shunt matching network; and 
     FIG. 19 is a Smith chart showing the simulated impedance of the slotted PIFA of FIG. 15 with a shunt matching network over the frequency range 2000 to 2900 MHz. 
    
    
     In the drawings the same reference numerals have been used to indicate corresponding features. 
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     A perspective view of a PIFA mounted on a handset is shown in FIG.  1 . The PIFA comprises a rectangular patch conductor  102  supported parallel to a ground plane  104  forming part of the handset. The antenna is fed via a feed pin  106 , and connected to the ground plane  104  by a shorting pin  108 . 
     In a typical example embodiment of a PIFA the patch conductor  102  has dimensions 20×10 mm and is located 8 mm above the ground plane  104  which measures 40×100×1 mm. The feed pin  106  is located at a corner of both the patch conductor  102  and ground plane  104 , and the shorting pin  108  is separated from the feed pin  106  by 3 mm. The return loss S 11  of this embodiment (without matching) was simulated using the High Frequency Structure Simulator (HFSS), available from Ansoft Corporation, with the results shown in FIG. 2 for frequencies f between 1000 and 3000 MHz. A Smith chart illustrating the simulated impedance of this embodiment over the same frequency range is shown in FIG.  3 . 
     It can clearly be seen that the response is inductive at resonance. The reasons for this can be seen be modelling the PIFA as a very small, heavily top-loaded folded monopole antenna. This model is illustrated at the left hand side of FIG. 4, with the patch conductor  102  forming a top load parallel to the ground plane  104 , the feed pin  106 , fed by a voltage source  402  supplying a voltage V, forming one arm of the folded monopole and the shorting pin  108  forming the other arm of the folded monopole. 
     When the feed and shorting pins  106 ,  108  are within a fraction of a wavelength of one another, the antenna can be decomposed, as shown in FIG. 4, into common mode (radiating) and a differential mode (non-radiating) parts. In the common mode part both the feed pin  106  and the shorting pin  108  are fed by a voltage source  404  providing a voltage of V 12 , thereby generating respective currents I c1  and I c2  in the pins  106 ,  108 . The differential mode part is similar, but the voltage source  404  feeding the shorting pin  108  provides a voltage of −V/2, thereby generating nominally equal but oppositely-directed currents I d  in each of the pins  106 ,  108 . 
     The impedance of the common mode, Z c , is given approximately as 
     
       
         
           Z 
           c 
           =Z 
           m 
           +Z 
           h  
         
       
     
     where Z m  and Z h  are respectively the impedances of the monopole and handset over a perfectly conducting ground plane. The monopole comprises two closely coupled conductors (the feed and shorting pins  106 ,  108 ), and therefore has an increased diameter (and wider bandwidth). The impedance Z c  is related to the currents and voltages by          Z   c     =       V   /   2         I   c1     +     I   c2                                
     If the pins  106 ,  108  are of equal diameter the currents I c1  and I c2  will both be equal and can be denoted by I c , where          I   c     =     V     4        Z   c                                
     Hence, the current is approximately a quarter of the current that would be supplied to a monopole of the same length. 
     The impedance of the differential mode, Z d , is given by 
     
       
           Z   d   =jZ   0  tan(β x )  
       
     
     which is the well-known impedance of a short-circuit transmission line. The differential mode current is given by          I   d     =       V     Z   d       =     V     j                   Z   0          tan        (     β                 x     )                                    
     The total input current I is the sum of I c  and I d , which is        I   =       V     4        Z   c         +     V     j                   Z   0          tan        (     β                 x     )                                    
     Hence, the effective impedance of the structure is 4Z c  in parallel with Z d . The impedance of the monopole and handset is transformed to a higher value by the action of the fold in the (radiating) common mode, which allows the low resistance of a short monopole to be transformed up to 50 Ω, but with an accompanying increase in the capacitive reactance. This reactance can then be tuned out by the effect of the differential mode impedance, a short circuit stub having a length of less than a quarter wave being inductive. 
     As shown in FIG. 4 the pins  106 ,  108  are of equal diameter. However, it can be advantageous to use pins of different diameter (or of different cross-sectional area for pins having a non-circular cross-section) as this can provide an impedance transformation. For example, if the cross-sectional area of the feed pin  106  is reduced and that of the shorting pin  108  is increased, then I c1  is decreased and I c2  is increased. Hence, for the same total current, the current supplied to the feed pin  106  is reduced thereby increasing the impedance of the antenna. By varying the ratio of cross-sectional areas of the pins  106 ,  108  a range of impedances can be achieved. A similar effect can also be achieved by replacing one or both of the pins  106 ,  108  by a plurality of conductors of identical size, with each of the pins  106 ,  108  being replaced by a different number of conductors, or by some combination of the two approaches. 
     Simulations were performed driving the feed and shorting pins  106 ,  108  (of equal diameter) in common and differential mode. FIG. 5 shows the simulated return loss S 11  for frequencies f between 1000 and 3000 MHz and FIG. 6 is a Smith chart showing the simulated impedance over the same frequency range. In both figures the summed simulation results are shown by solid lines, while results for the common and differential modes are shown by dashed and dotted lines respectively. The differential mode response has been clipped since it displays a negative resistance at resonance, which is outside the bounds of a normal Smith chart. It is clear, from comparison with FIGS. 2 and 3, that the summation of the two modes gives results very similar to the original simulation, thereby demonstrating the validity of the approach. 
     It is also clear from FIG. 6 that the inductive response is caused by the shunt inductance of a short circuit transmission line formed between the feed pin  106  and shorting pin  108 . This inductance can be removed by providing a longer transmission line. FIG. 7 is a perspective view of PIFA mounted on a handset, which has been modified from that of FIG. 1 by the introduction of a slot  702  into the patch conductor  102 , thereby increasing the length of the transmission line. By positioning the slot centrally in the patch conductor  102  the four-times impedance transformation, provided by the folded monopole configuration, is maintained. 
     Simulations of the performance of the PIFA shown in FIG. 7 were performed, with results for return loss S 11  shown in FIG. 8 and a Smith chart shown in FIG.  9 . Simulations were also performed by common and differential mode analyses, as before, with results for return loss S 11  shown in FIG. 10 and a Smith chart shown in FIG. 11 (with the differential mode results clipped as in FIG.  6 ). Again, it is apparent that the common and differential mode analyses are appropriate. It is also clear from the Smith charts that the effect of the shunt reactance of the differential mode is greatly reduced by the incorporation of the slot  702 . It can be seen that a longer slot would be optimal, which could be achieved by meandering the slot on the patch conductor  102 . 
     The shapes of the S 11  response shown in FIGS. 8 and 9 (or  10  and  11 ) are clearly amenable to broadbanding using a conventional parallel LC resonant circuit connected in shunt with the antenna input. A series LC circuit connected in series with the input could also then be used. Alternatively, the length of the slot  702  could be arranged to be a quarter wavelength, thereby enabling the differential mode transmission line to be used for broadbanding purposes. A further advantage of this arrangement is that a quarter wavelength transmission line provides a high impedance, and therefore carries less current than the short, two pin transmission line of a known PIFA (which is low impedance), improving the efficiency of the antenna. 
     It is clear from the common mode analysis, and from the fact that the resistance at resonance is too high, that the antenna could be made to be lower profile. FIG. 12 is a perspective view of slotted PIFA mounted on a handset, which has been modified from that of FIG. 7 by reducing the separation of the patch conductor  102  and ground plane  104  from 8 mm to 2 mm. The slot  702  has also been moved closer to the edge of the patch conductor, thereby providing a significantly increased common mode impedance transformation. 
     Simulations of the performance of the PIFA shown in FIG. 12 were performed, with results for return loss S 11  shown in FIG. 13 and a Smith chart shown in FIG.  14 . The simulations demonstrate that a wide bandwidth is maintained despite the reduction in antenna volume. It is clear that further reductions in conductor separation (and therefore antenna volume) are possible. 
     FIG. 15 is a plan view of another slotted PIFA arrangement, suitable for a Bluetooth embodiment. The patch conductor  102  has dimensions 11.25×7.5 mm, is fed via a 0.5 mm-wide planar feed conductor  106  and grounded by a 0.5 mm-wide planar grounding conductor  108 . A first slot  1502 , located between the feed and ground conductors  106 ,  108 , has a width of 0.375 mm and a length of approximately 25 mm (nearly a quarter of a wavelength). This slot acts to increase the length of the transmission line between the conductors  106 ,  108 , as in previous embodiments. The slot  1502  is asymmetrically located in the patch  102 , located just 0.25 mm from the edge of the patch, thereby providing a significant impedance transformation. A second slot  1504  is also provided in the patch conductor  102 . This slot merely acts to increase the effective length of the patch  102 . 
     Simulations were performed to predict the performance of the PIFA shown in FIG. 15 mounted 1 mm above the top left hand corner of a ground conductor having dimensions 100×40×1 mm (as in previous embodiments). Results for return loss S 11  are shown in FIG. 16 and a Smith chart is shown in FIG.  17 . The simulations show that a reasonable bandwidth is achieved, the Smith chart demonstrating some potential for broadbanding. 
     Further simulations of this PIFA were performed with the addition of a shunt matching network comprising a 0.25 nH inductor and a 16 pF capacitor in parallel. Results for return loss S 11  are shown in FIG. 18 and a Smith chart is shown in FIG.  19 . It is clear that the matching has significantly improved both the match and bandwidth of the antenna, and there is the potential for further improvements by the addition of a series resonant circuit. 
     The results of the PIFA of FIG. 15 are particularly impressive taking into account its volume, which is significantly smaller than prior art antennas of equivalent performance. The dimensions are small enough for potential integration with Bluetooth modules, providing significant advantages in miniaturisation. 
     From reading the present disclosure, other modifications will be apparent to persons skilled in the art. Such modifications may involve other features which are already known in the design, manufacture and use of antenna arrangements and component parts thereof, and which may be used instead of or in addition to features already described herein. 
     In the present specification and claims the word “a” or “an” preceding an element does not exclude the presence of a plurality of such elements. Further, the word “comprising” does not exclude the presence of other elements or steps than those listed.