Abstract:
One problem addressed by the present invention is to provide an optical sensor, a solid-state imaging device, and methods for reading the signals therefrom, which contribute greatly to the development of industry and the realization of a safer and more secure society. One solution according to the present invention is an optical sensor having a light-receiving element, storage capacitors that store a charge, and a transfer switch for transferring to the storage capacitors a charge generated by light input to the light-receiving element, wherein the storage capacitors are a floating diffusion capacitor and a lateral overflow integration capacitor, and the transfer switch is a non-LDD/MOS transistor, that is, a non-LDD/MOS transistor for which the impurity concentration of the drain region is reduced by 50%.

Description:
BACKGROUND OF THE INVENTION 
     Field of the Invention 
       [0001]    The present invention relates to an optical sensor, a signal reading method therefor, a solid-state imaging device, and a signal reading method therefor. 
       Description of the Background Art 
       [0002]    With advancements in science and technology as well as the widespread availability of the Internet, demands for optical sensors and solid-state imaging devices have expanded dramatically. Meanwhile, optical sensors having high sensitivity, high speed, wide dynamic range, and broad optical wavelength band compatibility as well as still image and video compatible solid-state imaging devices are in strong demand in the market as must-haves for the development of new markets. In particular, optical sensors having a wider dynamic range and solid-state imaging devices are desired in markets such as medical, pharmaceutical, health, and nursing markets, life science markets, and disaster prevention and crime prevention markets required for the formation of a safe and secure society. 
         [0003]    Examples of optical sensors having a wide dynamic range and solid-state imaging devices include those described in Patent Document 1. 
       PATENT DOCUMENTS 
       [0000]    
       
         Patent Document 1: Japanese Laid-Open Patent Application No. 2005-328493 
       
     
       SUMMARY OF THE INVENTION 
     Problems to be Solved by the Invention 
       [0005]    Nevertheless, while the optical sensor and the solid-state imaging device described in Patent Document 1 certainly have a wide dynamic range compared to conventional products, the widened area of the dynamic range is on the high illumination side while the low illumination side remains in the conventional realm. Thus, markets that also require support in the low light intensity range remain underserved. As a result, further industry development and the realization of a safer and more secure society are still significant issues in the international community. 
         [0006]    The present invention has been made in view of the above, and it is therefore a main object of the present invention to provide an optical sensor, a solid-state imaging device, and methods for reading the signals therefrom, which contribute greatly to the development of industry and the realization of a safer and more secure society. 
         [0007]    It is another object of the present invention to provide an optical sensor having a wide dynamic range performance that allows detection from a single photon, a solid-state imaging device, and methods for reading the signals therefrom. 
         [0008]    It is yet another object of the present invention to provide an optical sensor having a dynamic range, from a single-photon light intensity range to a high illumination light intensity range, as well as high sensitivity, high speed, and broad optical wavelength band compatibility, a solid-state imaging device, and methods for reading the signals therefrom. 
         [0009]    It is yet another object of the present invention to provide an optical sensor having a wide dynamic range performance that achieves both a high sensitivity performance and an adequate high saturation performance that allow single photon detection, as well as high sensitivity, high speed, and broad optical wavelength band compatibility, a solid-state imaging device, and methods for reading the signals therefrom. 
       Means for Solving the Problems 
       [0010]    The present invention is the result of extensive efforts in research and development in view of the above, and one aspect of the present invention is an optical sensor comprising a light-receiving element, storage capacitors that store a charge, and a transfer switch for transferring to the storage capacitors a charge generated by light input to the light-receiving element, wherein the storage capacitors are a floating diffusion capacitor and a lateral overflow integration capacitor, and the transfer switch is a non-LDD/MOS transistor for which the impurity concentration of a drain region thereof is 1×10 2  impurities/cm 3  or less. 
         [0011]    Another aspect of the present invention is an optical sensor comprising a light-receiving element (PD), a transfer switch (T), an overflow switch (S), and a reset switch (R) connected in series in that order; 
         [0012]    a floating diffusion capacitor (CD) and a source follower switch (SF) connected to wiring between the transfer switch (T) and the switch (S); and 
         [0013]    a lateral overflow integration capacitor (C LOFIC ) connected to wiring between the switch (S) and the reset switch (R); wherein 
         [0014]    the source follower switch (SF) is a MOS transistor, and the transfer switch (T) is a non-LDD/MOS transistor for which the impurity concentration of a drain region is 50% less than an impurity concentration of a source region of the source follower switch (SF). 
         [0015]    Yet another aspect of the present invention is an optical sensor comprising a light-receiving element, storage capacitors that store a charge, a transfer switch for transferring to the storage capacitors a charge generated by light input to the light-receiving element, and a pixel signal output line per pixel; and 
         [0016]    a signal reading path connected to the pixel signal output lines; wherein: 
         [0017]    the storage capacitors are a floating diffusion capacitor and a lateral overflow integration capacitor, and the transfer switch is a non-LDD/MOS transistor for which the impurity concentration of a drain region thereof is 1×10 20  impurities/cm 3  or less; 
         [0018]    the signal reading path receives a first pixel output signal subjected to charge-voltage conversion by the floating diffusion capacitor, and a second pixel output signal subjected to charge-voltage conversion by combining the floating diffusion capacitor and the lateral overflow integration capacitor; and 
         [0019]    the first pixel output signal is amplified in the signal reading path by a plurality of amplifiers that include at least one amplifier having an amplification factor greater than 1. 
         [0020]    Yet another aspect of the present invention is a multi-pixel optical sensor comprising a light-receiving element, storage capacitors that store a charge, and a transfer switch for transferring to the storage capacitors a charge generated by light input to the light-receiving element, the storage capacitors being a floating diffusion capacitor and a lateral overflow integration capacitor, and the transfer switch being a non-LDD/MOS transistor for which an impurity concentration of a drain region thereof is 1×10 20  impurities/cm 3  or less; 
         [0021]    pixel column portions having pixel portions planarly arranged therein; 
         [0022]    a pixel signal output line having the pixel column portions connected sequentially thereto; and 
         [0023]    a signal reading path portion connected to the pixel signal output at a position downstream from a position where a last pixel portion of an array of the pixel column portions of the pixel signal output line is connected; wherein: 
         [0024]    the signal reading path portion comprises a plurality of signal paths, and at least two of the plurality of signal paths are respectively provided with amplification functions having different amplification factors; and 
         [0025]    at least one of the amplification functions has an amplification factor greater than 1. 
         [0026]    Yet another aspect of the present invention is a signal reading method for an optical sensor comprising a light-receiving element, storage capacitors that store a charge, and a transfer switch for transferring to the storage capacitors a charge generated by light input to the light-receiving element, per pixel portion; 
         [0027]    a sensor portion in which the storage capacitors are a floating diffusion capacitor and a lateral overflow integration capacitor, and the transfer switch is a non-LDD/MOS transistor for which the impurity concentration of a drain region thereof is 1×10 20  impurities/cm 3  or less; 
         [0028]    a pixel signal output line having each pixel portion connected thereto; and 
         [0029]    a signal reading path connected to the pixel signal output line; 
         [0030]    the signal reading method comprising the steps of: 
         [0031]    forming a first pixel output signal by converting a charge of a charge amount that contributes to reading by the floating diffusion capacitor to voltage, forming a second pixel output signal by combining the floating diffusion capacitor and the lateral overflow integration capacitor and converting a charge of a charge amount that contributes to reading to voltage, and inputting these two pixel output signals to the signal reading path; wherein: 
         [0032]    the first pixel output signal is amplified in the signal reading path by a plurality of amplifiers that include at least one amplifier having an amplification factor greater than 1. 
         [0033]    Yet another aspect of the present invention is an imaging device comprising a light-receiving element (PD), a transfer switch (T), an overflow switch (S), and a reset switch (R) connected in series in that order, a floating diffusion capacitor (C FD ) and a source follower switch (SF) connected to wiring between the transfer switch (T) and the switch (S), and a lateral overflow integration capacitor (C LOFIC ) connected to wiring between the switch (S) and the reset switch (R), wherein: 
         [0034]    the source follower switch (SF) is a MOS transistor; 
         [0035]    the transfer switch (T) comprises a plurality of pixel portions serving as non-LDD/MOS transistors for which the impurity concentration of a drain region is 50% less than an impurity concentration of a source region of the source follower switch (SF), and the light-receiving elements (PD) of the plurality of pixel portions are arranged two-dimensionally and comprise a pixel array; 
         [0036]    the plurality of pixel portions comprises pixel column output signal lines that are sequentially connected; 
         [0037]    the pixel column output signal line comprises a column circuit portion connected thereto, and the column circuit portion receives a first pixel output signal subjected to charge-voltage conversion by the floating diffusion capacitor, and a second pixel output signal subjected to charge-voltage conversion by combining the floating diffusion capacitor and the lateral overflow integration capacitor; and 
         [0038]    the first pixel output signal is amplified in the signal reading path by a plurality of amplifiers that include at least one amplifier having an amplification factor greater than 1. 
         [0039]    Yet another aspect of the present invention is a signal reading method for an imaging device comprising a light-receiving element (PD), a transfer switch (T), an overflow switch (S), and a reset switch (R) connected in series in that order, a floating diffusion capacitor (C FD ) and a source follower switch (SF) connected to wiring between the transfer switch (T) and the switch (S), and a lateral overflow integration capacitor (C LOFIC ) connected to wiring between the switch (S) and the reset switch (R), wherein: 
         [0040]    the source follower switch (SF) is a MOS transistor, the transfer switch (T) comprises a plurality of pixel portions serving as non-LDD/MOS transistors for which the impurity concentration of a drain region is 50% less than an impurity concentration of a source region of the source follower switch (SF), the light-receiving elements (PD) of the plurality of pixel portions are arranged two-dimensionally to constitute a pixel array, the plurality of pixel portions is sequentially connected to a pixel column output signal line, and the pixel column output signal line is connected to a column circuit portion; 
         [0041]    the signal reading method comprising the steps of: 
         [0042]    forming a first pixel output signal by converting a charge of a charge amount that contributes to reading by the floating diffusion capacitor to voltage, forming a second pixel output signal by combining the floating diffusion capacitor and the lateral overflow integration capacitor and converting a charge of a charge amount that contributes to reading to voltage, and inputting these two pixel output signals to the signal reading path; wherein: 
         [0043]    the first pixel output signal is amplified in the signal reading path by a plurality of amplifiers that include at least one amplifier having an amplification factor greater than 1. 
       Effect of the Invention 
       [0044]    According to the present invention, it is possible to provide an optical sensor having a wide dynamic range performance, from a single photon light intensity range to a high illumination light intensity range, as well as high sensitivity, high speed, and broad optical wavelength band compatibility, a solid-state imaging device, and driving methods thereof, making it possible to contribute greatly to the development of industry and the realization of a safer and more secure society. 
     
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         [0045]      FIG. 1  is a circuit diagram illustrating an example of preferred embodiment of a pixel circuit and one column of reading circuits of a CMOS image sensor according to the present invention. 
           [0046]      FIG. 2  is an equivalent circuit diagram illustrating a pixel circuit portion extracted from the circuit diagram illustrated in  FIG. 1 . 
           [0047]      FIG. 3A  is a schematic structural cross-sectional view for explaining a normal structure of a MOS transistor. 
           [0048]      FIG. 3B  is a schematic structural cross-sectional view for explaining a structure of a MOS transistor according to the present invention. 
           [0049]      FIG. 4A  is a schematic structural cross-sectional view schematically illustrating an expanse of a width W of a depletion layer formed when a diffusion layer having a normal impurity concentration is provided. 
           [0050]      FIG. 4B  is a schematic structural cross-sectional view schematically illustrating the expanse of the width W of the depletion layer formed when a diffusion layer having an impurity concentration reduced to a value lower than normal is provided as in the present invention. 
           [0051]      FIG. 5  is a schematic modification cross-sectional view for explaining a device structure layout when LDD formation is omitted and a concentration reduction of the diffusion layer is applied to a device comprising a pixel circuit portion  101  illustrated in  FIG. 2 . 
           [0052]      FIG. 6A  is a schematic step diagram for explaining a manufacturing example of an optical input sensor pixel portion  500 . 
           [0053]      FIG. 6B  is a schematic step diagram following  FIG. 6A . 
           [0054]      FIG. 6C  is a schematic step diagram following  FIG. 6B . 
           [0055]      FIG. 6D  is a schematic step diagram following  FIG. 6C . 
           [0056]      FIG. 6E  is a schematic step diagram following  FIG. 6D . 
           [0057]      FIG. 6F  is a schematic step diagram following  FIG. 6E . 
           [0058]      FIG. 6G  is a schematic step diagram following  FIG. 6F . 
           [0059]      FIG. 6H  is a schematic step diagram following  FIG. 6H . 
           [0060]      FIG. 6I  is a schematic step diagram following  FIG. 6H . 
           [0061]      FIG. 6J  is a schematic step diagram following  FIG. 6 . 
           [0062]      FIG. 6K  is a schematic step diagram following  FIG. 6K . 
           [0063]      FIG. 6L  is a schematic step diagram following  FIG. 6K . 
           [0064]      FIG. 7  is a schematic explanatory conceptual view for explaining photoelectric conversion characteristics of a first (1-1) signal, a first (1-2) signal, and a second signal. 
           [0065]      FIG. 8  is a graph showing the relationship between a number of noise electrons of floating diffusion input conversion and an erroneous reading probability. 
           [0066]      FIG. 9  is a graph showing the relationship between the number of input conversion noise electrons and a charge-voltage conversion gain. 
           [0067]      FIG. 10  is a timing diagram when a signal of one pixel is read. 
           [0068]      FIG. 11  is a flowchart for explaining a procedure when a signal of one pixel is read. 
           [0069]      FIG. 12  illustrates an example of a preferred embodiment of a sensor portion in a case where the CMOS image sensor according to the present invention is applied to an imaging device, and is a circuit diagram illustrating N pixel circuits of a first column and one column of reading circuits. 
           [0070]      FIG. 13  is an overall block diagram schematically illustrating the entire sensor portion of the imaging device illustrated in  FIG. 12 . 
           [0071]      FIG. 14  is a diagram illustrating an example of a schematic layout pattern of pixel selection switch means (X)  207  and source follower switch means (SF)  208 . 
           [0072]      FIG. 15  is a diagram illustrating another example of a schematic layout pattern of the pixel selection switch means (X)  207  and the source follower switch means (SF)  208 . 
           [0073]      FIG. 16  is a diagram illustrating yet another example of a schematic layout pattern of the pixel selection switch means (X)  207  and the source follower switch means (SF)  208 . 
       
    
    
     DESCRIPTION OF THE PREFERRED EMBODIMENTS 
       [0074]      FIG. 1  illustrates a circuit diagram serving as an example of a preferred embodiment (embodiment 1) illustrating a pixel circuit and one column of reading circuits of a CMOS optical input sensor according to the present invention. 
         [0075]    With the circuit configuration in  FIG. 1  and a device structure described later, it is possible to achieve both high sensitivity and high saturation for photon detection. 
         [0076]    To avoid complexities in illustration and explanation,  FIG. 1  illustrates the minimum parts required for a bare minimum explanation that will allow the aspects of the present invention to be plainly understood. 
         [0077]    A circuit  100  in  FIG. 1  comprises a pixel circuit portion  101  and a column circuit portion  102 . 
         [0078]    The pixel circuit portion  101  and the column circuit portion  102  are electrically connected via a pixel column output signal line  103 . A current source  108  is provided below the pixel column output signal line  103 . The current source  108  comprises a MOS transistor, for example. 
         [0079]    The equivalent circuit diagram of the pixel circuit portion  101  is equivalent to the pixel equivalent circuit diagram in FIG. 21 of Patent Document 1. In the example in  FIG. 1 , the column circuit portion  102  comprises three column reading circuits. A first column reading circuit  102 HG for outputting a first (1-1) signal  102 S 1  is configured by arranging switch means (SW/AMPEN)  104 HG, a high-gain amplifier  105 HG, and an analog memory circuit portion  106 HG for reading the first (1-1) signal  102 S 1 , in that order from the upstream side, and electrically connecting the same using a signal line  107 HG. 
         [0080]    In the analog memory circuit portion  106 HG, switch means (NS 1 H)  106 HG- 1  and a capacitor (N 1 H)  106 HG- 2  as well as switch means (SS 1 H)  106 HG- 3  and a capacitor (S 1 H)  106 HG- 4  for the first (1-1) signal  102 S 1  are respectively electrically connected in series, and connected as illustrated to the signal line  107 HG. 
         [0081]    A second column reading circuit  102 LG for outputting a first (1-2) signal  10252  is configured by arranging switch means (SW/AMPEN)  104 LG, a low-gain amplifier  10 SLG, and an analog memory circuit portion  106 LG for reading the first (1-2) signal  102 S 2 , in that order from the upstream side, and electrically connecting the same using a signal line  107 LG. 
         [0082]    In the analog memory circuit portion  106 LG, switch means (NS 1 )  106 LG- 1  and a capacitor (N 1 )  106 LG- 2  as well as switch means (SS 1 )  106 LG- 3  and a capacitor (S 1 )  106 LG- 4  are respectively electrically connected in series, and connected as illustrated to the signal line  107 LG. 
         [0083]    In a third column reading circuit  102 N that outputs a second signal  102 SN, unlike the first column reading circuit  102 HG and the second column reading circuit  102 LG, an analog memory circuit portion  106 N is directly electrically connected to the pixel output signal line  103  via a signal line  107 N 1 . 
         [0084]    In the analog memory circuit portion  106 N, switch means (NS 2 )  106 N- 1  and a capacitor (N 2 )  106 N- 2  as well as switch means (SS 2 )  106 N- 3  and a capacitor (S 2 )  106 N- 4  are respectively electrically connected in series, and connected as illustrated to a signal line  107 N 2 . 
         [0085]    The column circuit portion  102  is common to each pixel circuit portion of one column. 
         [0086]    With the circuit configuration in  FIG. 1 , it is possible to achieve both high sensitivity characteristics and high saturation characteristics of single photon detection, making it possible to provide a highly sensitive image sensor having a wide dynamic range performance. 
         [0087]    In the example in  FIG. 1 , a total of three signal paths including a path via a high-gain amplifier (first column reading circuit portion  102 HG), a path via a low-gain amplifier (second column reading circuit portion  102 LG), and a path that directly connects the pixel signal output line (third column reading circuit portion  102 N) are provided to each column, and two analog memories are arranged in each path. 
         [0088]    The two gain amplifiers arranged in the column are used when the highly sensitive first signal is read from the pixel circuit portion  101 , and produce the first (1-1) signal obtained by increasing the amplitude and reducing a later-stage noise and the first (1-2) signal having a signal amplitude left as is, thereby making it possible to obtain an ultra-highly sensitive signal and a highly sensitive signal. Further, the highly saturated second signal obtained by the pixel circuit portion  101  is read at a signal amplitude left as is using a path that directly connects the pixel signal output line, making it possible to obtain a highly saturated signal. That is, based on the three signals described above, the ultra-highly sensitive first (1-1) signal is used with extremely low illumination pixels, the second signal is used with high illumination pixels, and the first (1-2) signal is used with illumination pixels therebetween, making it possible to obtain video signals linearly using a single exposure period, from an extremely low illumination region to high illumination. 
         [0089]    The letters of a reference number in the descriptions of  FIG. 1  have the following technical meanings: 
         [0000]    AMPEN: Switch for reading “first (1-1) signal” and “first (1-2) signal”
 
NS 1 H: Switch for sampling “first (1-1) BG signal”
 
SS 1 H: Switch for sampling “first (1-1) optical signal”
 
N 1 H: Capacitor for holding “first (1-1) BG signal”
 
S 1 H Capacitor for holding “first (1-1) optical signal”
 
NS 1 : Switch for sampling “first (1-2) BG signal”
 
SS 1 : Switch for sampling “first (1-2) optical signal”
 
N 1 : Capacitor for holding “first (1-2) BG signal”
 
S 1 : Capacitor for holding “first (1-2) optical signal”
 
NS 2 : Switch for sampling “second BG signal”
 
SS 2 : Switch for sampling “second optical signal”
 
N 2 : Capacitor for holding “second BG signal”
 
S 2 : Capacitor for holding “second optical signal”
 
         [0090]    The aspects of the present invention will now be described in accordance with  FIGS. 2, 3A, 3B, 4A, and 4B . 
         [0091]      FIG. 2  illustrates the pixel circuit portion  101  in the circuit  100  illustrated in  FIG. 1 . 
         [0092]    The pixel circuit portion  101  comprises a photodiode (PD)  201 , transfer switch means (T)  202 , a floating diffusion capacitor (C FD ; also referred to as “C FD  capacitor”)  203  that performs charge-voltage conversion, a lateral overflow integration capacitor (C LOFIC )  204 , overflow switch means (S) 205, reset switch means (R)  206 , pixel selection switch means (X)  207 , and source follower switch means (SF)  208 . 
         [0093]    The overflow switch means (S)  205  is an overflow switch that combines or splits the potential of the C FD  capacitor  203  and the lateral overflow integration capacitor (C LOFIC )  204 . 
         [0094]    In  FIG. 2 , “VR” refers to reset voltage, and “VDD” refers to power source voltage. 
         [0095]    In the present invention, the pixel circuit portion  101  is provided with the C LOFIC  capacitor  204 , and thus hereinafter is also referred to as the “LOFIC pixel portion.” 
         [0096]    Each switch means in the pixel circuit portion  101  in the present invention preferably comprises a field effect transistor (FET) such as a metal oxide semiconductor (MOS) transistor (MOSTr). 
         [0097]    In  FIG. 2 , each of the switch means, including the transfer switch means (T)  202 , the overflow switch means (S)  205 , the reset switch means (R)  206 , the pixel selection switch means (X)  207 , and the source follower switch means (SF)  208  comprises a MOSTr. 
         [0098]    The basic signal path in the present invention is as follows. 
         [0099]    That is, light input to the PD  201  generates a photocharge, and the generated photocharge is converted to voltage using the capacitance of the Cm  203  and the total capacitance of the Cm  203  and the C LOFIC    204 , read to the corresponding analog memory circuit portion of the analog memory circuit portions  106 HG,  106 LG,  106 N via the SF  208 , and held as a voltage signal in the analog memory of the analog memory circuit portion. Subsequently, the capacitance of the voltage signal is split from analog memory, read to an area outside the device via an output buffer (not illustrated), and converted to a digital signal by an analog-digital converter (ADC; not illustrated). 
         [0100]    In this series of signal paths, noise is increasingly superimposed in the later stages of reading, causing a decrease in S/N. In the present invention, therefore, the charge-voltage conversion gain of the earliest stage possible of the reading path, particularly the C FD    203 , is increased to the extent possible, thereby relatively reducing the noise of later stages of the reading path and increasing the S/N. 
         [0101]    The present invention was made on the basis of the discovery that, in the repeatedly performed process of actually repeatedly designing and manufacturing an input sensor device, measuring the sensitivity characteristics of the sensor, analyzing and investigating the results, and then feeding back the investigation results to design and manufacturing on the basis of the pixel circuit portion  101  illustrated in  FIG. 2 , the object of the present invention was achieved if the (gate) overlap capacitors indicated by the dashed circles in  FIG. 2  were optimized. 
         [0102]    The capacitance constituting the capacitor (C FD )  203  can be broadly divided into five types: a wiring parasitic capacitance (1) formed in a wiring portion of the device, a PN junction capacitance (2) formed in the FD diffusion layer portion, a gate/substrate parasitic capacitance (3) formed in the pixel SF portion, a channel capacitance (4), and a gate overlap capacitance (5) formed in the FD diffusion layer portion and the pixel SF portion. 
         [0103]    Among the five capacitance types that constitute the capacitor (C FD )  203 , the wiring parasitic capacitance (1) can be minimized to a certain extent by closely wiring an FD diffusion layer portion  504  and a pixel SF portion  505  to shorten the wiring distance, and separating adjacent metal wiring to the extent possible. However, taking into consideration the fact that the size of the pixel circuit portion  101  (hereinafter also referred to as “pixel size”) must be reduced on the basis of demands for increased device density, there is also a limit to the reduction of the wiring parasitic capacitance (1). 
         [0104]    As a method for improving the gate/substrate parasitic capacitance (3), the gate/substrate parasitic capacitance (3) can be reduced by applying a special process called “Well in Well” to the pixel SF portion  505 . However, due to problematic increases in process complexity and pixel size, adoption of the “Well in Well” process does not achieve both pixel size reduction and capacitance reduction. 
         [0105]    Additionally, according to investigations of the present inventors, the gate/substrate parasitic capacitance (3) is small compared to other capacitance values, and thus the conclusion has been made that there is no need to improve the gate/substrate parasitic capacitance (3) at this point in time. 
         [0106]    With regard to the channel capacitance (4), a channel for the flow of a constant current in the pixel SF portion  505  is required, and thus a substantial reduction in capacitance cannot be expected. 
         [0107]    Given “Cchl” as the channel capacitance of the source follower switch means  208 , the impact of the capacitance (Cchl) on the capacitor (C FD )  203  is on the basis of a mirror effect, and thus the channel capacitance (4) is, in effect, a multiple of “1—Gain of the source follower switch means  208 .” Thus, the channel capacitance (4) can be suppressed by utilizing the “Well in Well” process as described previously, removing the substrate bias effect, and setting the gain of the source follower switch means  208  to “1.” However, with adoption of the “Well in Well” process both pixel size reduction and capacitance reduction are not achieved. 
         [0108]    On the other hand, reduction of the PN junction capacitance (2) and gate overlap capacitance (5) cannot be expected using device layout or reading method schemes, and thus is improved in the present invention by changing the manufacturing process as described below. That is, in the present invention, reduction of the capacitance of the C FD    203  is optimized by significantly changing the conventional method so that the process of formation of the gate overlap capacitance (5) and the conditions thereof are as described later. 
         [0109]    The aspects of the present invention will first be described with regard to omission of a lightly doped drain (LDD) made for reducing the gate overlap capacitance, using  FIGS. 3A and 38 . 
         [0110]      FIG. 3A  is a schematic structural cross-sectional view for explaining the structure of normal MOSTrs  301 A 1 ,  301 A 2 . 
         [0111]      FIG. 3B  is a schematic structural cross-sectional view for explaining the structure of MOSTrs  301 B 1 ,  301 B 2  according to the present invention. 
         [0112]    Normally, first formation of an LDD  305  is performed between creations of gate electrodes  303 A,  303 B, and creations of side walls  304 A,  304 B 1 ,  304 B 2 . 
         [0113]    Next, the side walls  304 A,  304 B 1 ,  304 B 2  are formed and a diffusion layer  302  is formed, in that order. The reason for providing the LDDs  305  is to prevent hot carrier deterioration of the formed MOSTrs. That is, a part of electrons that travel from the source to the drain are accelerated by a strong electric field near the drain and become hot carriers having high energy. The hot carriers generate high-energy electrons and holes by impact ionization, produce flaws near the boundary between the gate insulation film and semiconductor, or are injected into the gate insulation film and captured in flaws in the gate insulation film, resulting in a fixed charge and leading to the deterioration of the electrical characteristics of the transistor over time. This generation of hot carriers is remarkable in transistors having a channel length of 1 μm or less, and is a significant problem in general logic LSI miniaturization. 
         [0114]    To suppress the generation of such hot carriers, a low-concentration diffusion layer for alleviating the electric field near the drain is formed. This is generally called an “LDD transistor.” Additionally, in this specification, a transistor that does not have an LDD structure is also called a “non-LDD transistor.” 
         [0115]    With such an LDD transistor, problems such as the following occur. 
         [0116]    As illustrated in  FIG. 3A , the sections resulting from the LDDs  305  in the diffusion layer  302  section form sections that extend to the gate electrode  303 A,  303 B sides (indicated by the sections of the LDDs  305  that extend to both sides of the diffusion layer  302 ), causing the gate overlap capacitance to increase. 
         [0117]    Here, in the present invention, with omission of formation of the LDDs  305 , one factor for significantly reducing overlap capacitance was discovered. Furthermore, through transistor trial manufacture and measurement tests, it was discovered that, under the operating voltage conditions of the optical sensor, the impact of the hot carriers previously described is sufficiently small and thus problems do not arise even when formation of the LDDs  305  is omitted. 
         [0118]      FIG. 3B  illustrates an enlarged view of the gate overlap portion with formation of the LDD  305   s  omitted. 
         [0119]    The process changes made for capacitance reduction are described below. 
         [0120]    The PN junction capacitance is determined by the width of the depletion layer formed across the p-epi layer and the n +  layer (diffusion layer). That is, the PN junction capacitance decreases as a width W of the depletion layer increases. The width W of this depletion layer is determined by the concentration of impurities in the p-epi layer and the n +  layer. 
         [0121]    In the present invention, the width W of the depletion layer is increased by decreasing the concentration of the impurities in the n +  layer, thereby decreasing the PN junction capacitance. 
         [0122]      FIGS. 4A and 4B  schematically illustrate the expanse of the width W of the depletion layer formed when a diffusion layer  402 A having a normal impurity concentration is provided, and when a diffusion layer  402 B having an impurity concentration reduced to a value lower than normal as in the present invention is provided, respectively. 
         [0123]      FIG. 4A  is a schematic structural cross-sectional view schematically illustrating the expanse of the width W of the depletion layer formed when a diffusion layer having a normal impurity concentration is provided to the MOSTr with LDD formation omitted. 
         [0124]      FIG. 4B  is a schematic structural cross-sectional view schematically illustrating the expanse of the width W of the depletion layer formed when a diffusion layer having a impurity concentration reduced to a value lower than normal is provided to the MOSTr with LDD formation omitted as in the present invention. 
         [0125]      FIG. 4A  illustrates a part of the structures of MOSTr  401 A 1  and MOSTr  401 A 2 . 
         [0126]    The diffusion layer  402 A comprises both a drain region (left side section of the diffusion layer  402 A in the figure) of the MOSTr  401 A 1 , and a source region (right side section of the diffusion layer  402 A in the figure) of the MOSTr  401 A 2 . 
         [0127]    When the concentration of impurities in the diffusion layer  402 A is high as usual, the width W of the depletion layer decreases as illustrated in  FIG. 4A . When the concentration of the impurities in the diffusion layer  402 B is low as in this specification, the width W of the depletion layer increases as illustrated in  FIG. 4B . 
         [0128]    The reduction in concentration of the impurities in the n +  layer (diffusion layer) widens the depletion layer width of the PN junction, and thus has the effect of reducing PN junction capacitance. Furthermore, the distance between charge and the gate electrodes in the n +  layer increases, resulting in the effect of reducing the gate overlap capacitance in the same way as omission of LDD formation. 
         [0129]      FIG. 5  illustrates a preferred example of an embodiment of the present invention when the omission of LDD formation and the concentration reduction of the diffusion layer are applied as described in  FIGS. 3A to 4B . 
         [0130]      FIG. 5  is a schematic modification cross-sectional view for explaining the device structure layout when the omission of LDD formation and the concentration reduction of the diffusion layer are applied to formation of the a device structure of an optical input sensor pixel portion  500  comprising the same circuit configuration as the circuit configuration of the pixel circuit portion  101  illustrated in  FIG. 2 . 
         [0131]    The extraction electrode (indicated by the solid line) in  FIG. 5  is illustrated as a virtual electrode. Further, components that are the same as those in  FIGS. 1 and 2  are denoted using the same reference numerals as  FIGS. 1 and 2 . 
         [0132]    The optical input sensor pixel portion  500  is obtained by epitaxially growing a p type silicon layer  500 - 2  on an n −  type silicon (n − Si) substrate  500 - 1 , and creating wiring with each electronic element, such as light-receiving diodes, transistors, and capacitive elements, on the basis of the circuit design illustrated in  FIG. 2 , utilizing the p type silicon layer  500 - 2 . 
         [0133]    In  FIG. 5 , the n type regions having a reduced doping amount of impurities compared to prior art in order to form a low capacitance FD are denoted by reference numerals  501 - 1 ,  501 - 2 ,  501 - 3 . 
         [0134]    Regions doped with impurity amounts at a high concentration as in prior art are n +  type regions  502 - 1 ,  502 - 2 ,  502 - 3 ,  502 - 4 ,  502 - 5 . 
         [0135]    Regions formed as LDDs as in prior art are n type regions  503 - 1 ,  503 - 2 ,  503 - 3 ,  503 - 4 ,  503 - 5 ,  503 - 6 . 
         [0136]    In the present invention, the n type regions ( 503 - 1  to  503 - 6 ) and the n +  type regions ( 502 - 1  to  502 - 5 ) described above are also referred to as “diffusion layers  502 - 1  to  502 - 5 .” 
         [0137]    Element isolation regions  506 - 1 ,  506 - 2 ,  506 - 3 ,  506 - 4  having the required performance characteristics are provided to those electronic elements in which thorough element isolation contributes to increased device performance. 
         [0138]    P type embedded regions  507 - 1 ,  507 - 2 ,  507 - 3  are provided to predetermined positions of the p type silicon layer  500 - 2 . 
         [0139]    In  FIG. 5 , the photodiode (PD)  201  comprises a diode structure in which an n −  region  508  and a p +  region  509  are layered. 
         [0140]    In the present invention, the photodiode (PD)  201  can also be changed to a phototransistor. 
         [0141]    Wiring ΦT is connected to an electrode  202 - 1  of the transfer switch means T 202 , wiring ΦS is connected to an electrode  205 - 1  of the overflow switch means S 205 , wiring ΦR is connected to an electrode  206 - 1  of the reset switch means R 206 , and wiring OX is connected to an electrode  207 - 1  of the pixel selection switch means (X)  207 . 
         [0142]    The n +  type region  502 - 1  functions as a drain of the reset switch means (R)  206 , and is connected to wiring V R  that imparts a reset voltage. 
         [0143]    An electrode  208 - 1  of the source follower switch means (SF)  208  is electrically connected to the n type region  501 - 1 . 
         [0144]    An electrode  204 - 1  of the lateral overflow integration capacitor (C LOFIC )  204  functions as one electrode of the capacitor (C LOFIC )  204 , and is electrically connected to the n type region  501 - 2 . 
         [0145]    The n +  type regions  502 - 2 ,  502 - 3  are directly electrically connected to wiring GND. 
         [0146]    The n +  type region  502 - 5  is directly electrically connected to the pixel output signal line  103 . 
         [0147]    Each of the switch means illustrated in  FIG. 5  comprises a MOSTr. 
         [0148]    The aspects of the present invention are an FD diffusion portion  504  and a pixel SF portion  505 . 
         [0149]    In the FD diffusion portion  504 , the conventional LDDs are omitted and the impurity concentration of the n type region  501 - 1  is reduced compared to prior art. As a result, reduction of the capacitance of the capacitor (C FD )  203  is effectively improved. 
         [0150]    In the n type region  501 - 3  of the pixel SF portion  505 , the LDDs are omitted to reduce the capacitance of the capacitor (C FD )  203 , and the impurity concentration is reduced compared to prior art. 
         [0151]    The n type region (diffusion layer)  501 - 2  is a diffusion layer connected to the capacitor (C LOFIC )  204 , and thus concentration reduction is improved to reduce the leak current to the capacitor (C LOFIC )  204  rather than to reduce the capacitance of the capacitor (C FD ). 
         [0152]    In the present invention, the degree to which the impurity concentrations of the n type regions  501 - 1 ,  501 - 3  are reduced is normally 50%, preferably 70%, and more preferably 90% with respect to the impurity contents of conventional practical elements (impurity contents of the n +  type regions  502 - 1  to  502 - 5 ). 
         [0153]    Specifically, the impurity concentration is 1×10 2  impurities/cm 3  or less, preferably 6×10 19  impurities/cm 3  or less, and more preferably 2×10 19  impurities/cm 3  or less. 
         [0154]    In the present invention, the reduction of the impurity concentration of the n type regions  501 - 1 ,  501 - 3  effectively improves the reduction of the capacitance of the capacitor (C FD )  203  as described above. However, reduction of the impurity concentrations of the n type regions  502 - 1 ,  502 - 4 ,  502 - 5 , for example, causes an increase in series resistance and, as a result, narrows the pixel signal output voltage range and thus decreases the dynamic range, decreases the gain of the source follower circuit and thus decreases the S/N ratio, or causes shading. Thus, reducing the impurity concentrations of the n type regions  502 - 1 ,  502 - 4 ,  502 - 5  to a greater degree than those of conventional practical elements is not favorable in terms of the total device design. 
         [0155]    From such perspectives, in the present invention, the impurity concentrations of the n type regions  501 - 1 ,  501 - 3  are preferably 50% or less than the impurity concentrations of the n +  type regions  502 - 1  to  502 - 5 . 
         [0156]    Such a device configuration as described above improves the capacitance reduction of the capacitor (C FD ), achieves both high sensitivity characteristics and high saturation characteristics of single photon detection, and allows provision of a highly sensitive image sensor having a wide dynamic range. 
         [0157]    Omitting the LDDs increases ON resistance, and conceivably decreases the current that flows to the transistors illustrated in  FIG. 5 . 
         [0158]    In particular, while the source follower switch means (SF)  208  requires the flow of a current of roughly several dozen μA to charge and discharge analog memory, verification of the impact of this increase in ON resistance revealed that such an increase is unproblematic in terms of practical use. 
         [0159]    The transfer switch means (T)  202 , the overflow switch means (S)  205 , and the reset switch means (R)  206  do not require large current flow since they are used only for transferring the charge stored in the photodiode (PD)  201  and resetting the capacitance of the photodiode (PD)  201 , the capacitance of the capacitor (C FD )  203 , and the capacitance of the capacitor (C LOFIC )  204  (total capacitance: about several dozen fF), and thus are not impacted by the above. 
         [0160]    When the series resistance of the source follower switch means (SF)  208  increases, the gain decreases. As a result, in the present invention, a decrease in gain is prevented by providing rather than omitting formation of the LDDs in the source portion of the MOS transistor of the switch means  208  as illustrated in  FIG. 5 , as in prior art. 
         [0161]    Thus, in the present invention, selectively omitting LDD formation in the MOS transistor constituting the capacitor (C FD )  203  reduces the gate overlap capacitance. 
         [0162]    Next, a manufacturing example of the optical input sensor pixel portion  500  illustrated in  FIG. 5  will be described using  FIGS. 6A to 6L . 
         [0163]    The manufacturing technique used is a normal semiconductor manufacturing technique, and thus descriptions are provided at a level that omits information (materials, chemicals, manufacturing conditions, manufacturing equipment, etc.) which is easily understood by a person skilled in the art. 
         [0164]    The Step List below indicates the main steps of the manufacturing process. 
         [0165]    However, in the steps below, step (9) is omitted in the present invention as described heretofore. 
         [0166]    Further, the steps (12) and (13) are steps for reducing the capacitance of the capacitor (C FD )  203 . 
       Step List 
       [0167]    Step (1): Element isolation (shallow trench isolation: STI) ( 506 - 1  to  506 - 4 ) formation
 
Step (2): Injection of well/channel stop layer ( 507 - 1  to  507 - 3 ,  510 ) formation ions
 
Step (3): Activating anneal
 
Step (4) Gate insulation film formation
 
Step (5): Gate electrode film formation
 
Step (6): Gate electrode patterning
 
Step (7): Injection of PD embedded n −  layer ( 508 ) formation ions
 
Step (8): Injection of PD surface p +  layer ( 509 ) formation ions
 
Step (9): Injection of lightly doped drain (LDD) formation ions Photolithographing→Ion injection→Resist removal
 
Step (10): Activating anneal
 
Step (11): Side wall formation
 
Step (12): Injection of S/D diffusion layer ( 501 - 1  to  501 - 3 ,  502 - 1  to  502 - 5 ) formation ions (1) Photolithographing→Ion injection→Resist removal
 
Step (13): Injection of S/D high-concentration diffusion layer ( 502 - 1  to  502 - 5 ) formation ions (2) Photolithographing→Ion injection→Resist removal
 
Step (14): Activating anneal
 
Step (15): First interlayer film ( 605 - 1 ) formation
 
Step (16): Contact hole formation
 
Step (17): Contact electrode ( 606 - 1  to  606 - 3 ) formation
 
Step (18): Metal electrode ( 607 - 1 ,  607 - 2 ) formation
 
Step (19): Hydrogen sintering
 
         [0168]      FIGS. 6A to 6L  illustrate step diagrams of the main points in the step order described above. 
         [0000]      FIG. 6A : Immediately after injection of PD surface p +  layer ( 509 ) formation ions
   FIG. 6B : Immediately after photolithographing for LDD formation ion injection
   FIG. 6C : Immediately after LDD formation ion injection
   FIG. 6D : Immediately after LDD formation ion injection and resist removal
   FIG. 6E : Immediately after side wall ( 602 - 1  to  602 - 11 ) formation
 
 FIG. 6F : Immediately after photolithographing for first ion injection during diffusion layer ( 501 - 1  to  501 - 3 ,  502 - 1  to  502 - 5 ) formation
 
 FIG. 6G : Immediately after first ion injection for diffusion layer ( 501 - 1  to  501 - 3 ,  502 - 1  to  502 - 5 ) formation
 
 FIG. 6H : Immediately after first ion injection and resist removal
 
 FIG. 6I : Immediately after photolithographing for second ion injection during diffusion layer ( 502 - 1  to  502 - 5 ) formation
 
 FIG. 6J : Immediately after second ion injection for diffusion layer ( 502 - 1  to  502 - 5 ) formation
 
 FIG. 6K : Immediately after second ion injection and resist removal
 
 FIG. 6L : Upon manufacturing process completion (equivalent to device structure in  FIG. 5 )
 
         [0169]    Next, a preferred example of a case where the present invention is applied to a highly sensitive CMOS image sensor (solid-state imaging device) as an image input device will be described using  FIGS. 1 and 2 . 
         [0170]    While a photoelectron detection type is described here, an element structure having a reverse polarity also naturally falls within the realm of the present invention. 
         [0171]    During a storage time (ST; the period in which a photocharge generated by the receipt of imaging light is stored to a predetermined capacitance), a supersaturation charge that flows out in a supersaturation state when storage into the photodiode (PD)  201  and the floating diffusion capacitor (C FD )  203  exceeds the respective capacitance values thereof is stored in the lateral overflow integration capacitor (C LOFIC )  204  via the overflow switch means (S)  205 . 
         [0172]    Charge-voltage conversion is performed in the capacitor (C FD )  203  having a small capacitance value, and a first signal A 1 - 1  is output from the pixel circuit portion. Next, at a large capacitance value obtained by adding together the capacitance of the floating diffusion capacitor (C FD )  203  and the capacitance of the lateral overflow integration capacitor (C LOFIC )  204 , charge-voltage conversion is performed, and a second signal A 1 - 2  is output from the pixel circuit portion. 
         [0173]    Here, the charge-voltage conversion performed in the capacitor (C FD )  203  having a small capacitance value, and the first signal A 1 - 1  from a pixel circuit portion A 1  is used for the imaging signal. 
         [0174]    From a pixel circuit portion A 2  having a large supersaturation charge as described above, the second signal A 1 - 2  is used for the imaging signal. 
         [0175]    The first signal A 1 - 1  is output from the column circuit portion  102  as a first (1-1) signal  102 S 1  and a first (1-2) signal  102 S 2  via the first column reading circuit  102 HG and the second column reading circuit  102 LG, respectively. 
         [0176]    In the prototype device of the present invention, the amplification factor of the high-gain amplifier  105 HG is 16×, and the amplification factor of the low-gain amplifier  105 LG is 1×, for example. 
         [0177]    However, to make the signal/noise ratio when the first (1-1) signal  102 S 1  and the first (1-2) signal  102 S 2  are synthesized greater than or equal to a fixed value for both the first (1-1) signal  102 S 1  and the first (1-2) signal  102 S 2 , a high signal amplification factor of the high-gain amplifier  105 HG is preferred to reduce the impact of the noise generated in the circuits downstream of column circuit portion  102 , when the difference between the amplification factors of the high-gain amplifier  105 HG and the low-gain amplifier  105 LG is within a fixed range. 
         [0178]    The second signal A 1 - 2  is output from the third column reading circuit  102 N as the second signal  102 SN. 
         [0179]    The signal output from the column circuit portion  102  is read upon sequential column selection by a scanning circuit (not illustrated) installed in the horizontal direction. 
         [0180]    Here, A/D conversion means (ADC) may be provided to each column reading circuit, each signal may be converted from analog to digital in each column inside the device chip, and the digital signal may be read to an area outside the device chip. 
         [0181]    From the above, it is possible to synthesize the highly sensitive first (1-1) signal  102 S 1 , the next highly sensitive first (1-2) signal  102 S 2 , and the highly saturated second signal  102 N and obtain a highly sensitive signal of the first (1-1) signal  102 S 1 , as well as an imaging signal in a wide dynamic range by one exposure period. 
         [0182]    That is, the signal obtained by synthesizing the “first (1-1) signal  102 S 1 ,” the “first (1-2) signal  102 S 2 ,” and the “second signal  102 N” is an “imaging signal,” and this “imaging signal” is obtained in a wide dynamic range at high sensitivity within one exposure period. In other words, the “imaging signal” is obtained in a wide range from a signal from a dark pixel of about one photon to a signal from a pixel having high illuminance within one exposure period.  FIG. 7  conceptually explains this point. 
         [0183]      FIG. 7  is a schematic explanatory conceptual view for explaining the photoelectric conversion characteristics of the first (1-1) signal  102 S 1 , the first (1-2) signal  102 S 2 , and the second signal  102 N. 
         [0184]      FIG. 8  is a graph showing the relationship between a number of noise electrons of floating diffusion input conversion and an erroneous reading probability. 
         [0185]    Here, a case where photocharges input to the floating diffusion were read one by one was considered correct reading. 
         [0186]    When the number of input conversion noise electrons was set to 0.26 or less, the erroneous reading probability could be made smaller than 5% and the signal could be read substantially unproblematically with a per photon accuracy. Further, it was also found that when the number of input conversion noise electrons was preferably set to 0.20 or less, the erroneous reading probability could be made smaller than 1%. 
         [0187]    These results were confirmed by repeated device design, simulation, manufacture, device driving, analysis, and investigation. 
         [0188]      FIG. 9  is a graph showing the relationship between the number of input conversion noise electrons and a charge-voltage conversion gain. 
         [0189]    The method for performing imaging using an imaging device according to the present invention and reading an image signal based on the obtained image will now be described using  FIGS. 10  and  11 . 
         [0190]    Here, the method for outputting a pixel signal of a device described below in the present invention is a method for outputting a pixel signal by a source follower circuit comprising the source follower switch (SF)  208  and the column current source  108 . 
         [0191]    The present invention is not limited to this pixel signal output method, and may be a floating capacitance load reading method for setting the pixel output line  103  into a floating state upon reset, driving the source follower switch (SF) by a capacitive load parasitic on the pixel output line  103 , and outputting a pixel signal. 
         [0192]      FIG. 10  is a timing diagram when a signal of one pixel is read. 
         [0193]    In  FIG. 10 , when the transfer switch means (T)  202  is turned ON and OFF (pulse ST 1 ) and then turned ON and OFF again (pulse ST 2 ), the period from the OFF moment of the first ON and OFF to the ON moment of the next ON and OFF is the storage time (ST). 
         [0194]    T 1  to T 5  each represent the timing of signal sampling completion of analog memory. 
         [0195]    Signal sampling of analog memory starts when the pulse is ON. 
         [0196]    During the period in which the overflow switch means (S)  205  and the pixel selection switch means (X)  207  maintain ON states for respective predetermined times (t 1 , t 2 ), the reset switch means (R)  206  and the transfer switch means (T)  202  turn ON sequentially, and maintain an ON state for respective predetermined times (t 3 , t 4 ). 
         [0197]    The OFF timings of the overflow switch means (S)  205  and the pixel selection switch means (X)  207  are such that, after the overflow switch means (S)  205  turns OFF, the pixel selection switch means (X)  207  turns OFF. 
         [0198]    Before the overflow switch means (S)  205  turns OFF, the reset switch means (R)  206  and the transfer switch means (T)  202  are turned ON and OFF (pulse S R1  and pulse S T1 ). 
         [0199]    The ON/OFF timing of the transfer switch means (T)  202  is within the ON/OFF period (“predetermined time (t 3 )”) of the reset switch means (R)  206 . 
         [0200]    After the transfer switch means (T)  202 , the reset switch means (R)  206 , and the overflow switch means (S)  205  sequentially turn OFF, the switch means (NS 2 )  106 N- 1  turns ON for a predetermined time (t 5 ). After the predetermined time (t 5 ) has elapsed, the switch means (NS 2 )  106 N- 1  turns OFF. 
         [0201]    The OFF timing of this switch means (NS 2 )  106 N- 1  is before the overflow switch means (S)  205  turns OFF. Subsequently, the pixel selection switch means (X)  207  turns OFF. 
         [0202]    When the pixel selection switch means (X)  207  turns ON once again, first the switch means (SW/AMPEN)  104 HG and the switch means (SW/AMPEN)  104 LG turn ON. 
         [0203]    Next, the switch means (NS 1 H)  106 HG- 1  and the switch means (NS 1 )  106 LG- 1  are simultaneously turned ON and OFF (pulse SHG 1  and pulse SLG 1 ). 
         [0204]    Next, the transfer switch means (T)  202  is turned ON and OFF (pulse ST 2 ), and subsequently the switch means (SS 1 H)  106 HG- 3  and the switch means (SS 1 )  106 LG- 3  are simultaneously turned ON. 
         [0205]    At the timing after the switch means (SS 1 H)  106 HG- 3  and the switch means (SS 1 )  106 LG- 3  simultaneously are turned OFF from this ON state, the switch means (SW/AMPEN)  104 HG and the switch means (SW/AMPEN)  104 LG are turned OFF (pulse SAM 1  and pulse SAM 2 ). 
         [0206]    After the switch means (SW/AMPEN)  104 HG and the switch means (SW/AMPEN)  104 LG are turned OFF, the overflow switch means (S)  205  is turned ON (pulse SS 2 ) and then the switch means (SS 2 )  106 N- 3  is turned ON and OFF (pulse SSS 2 ). 
         [0207]    Next, the reset switch means (R)  206  and the transfer switch means (T)  202  sequentially turn ON. 
         [0208]    During the period that this overflow switch means (S)  205  is ON (width t 1  of the pulse SS 2 ), the transfer switch means (T)  202  and the reset switch means (R)  206  sequentially turn OFF (pulse ST 3  and pulse SR 2 ). 
         [0209]    Next, the switch means (NS 2 )  106 N- 1  is turned ON and OFF (pulse SNS 22 ). After this switch means (NS 2 )  106 N- 1  is turned OFF (pulse SNS 22 ), the overflow switch means (S)  205  is turned OFF (pulse SS 2 ). 
         [0210]    Here, when a photocharge amount that exceeds the saturation charge amount of PD 201  generates in the PD  201  within the storage time (ST), the photocharge overflows from the PD  201  beyond a potential barrier of the transfer switch means (T)  202  and into the capacitor FD  203 . 
         [0211]    Furthermore, when the photocharge amount that exceeds the saturation charge amount of the capacitor FD  203  overflows into the capacitor FD  203 , the photocharge overflows from the capacitor (C FD )  203  beyond a potential barrier of the switch means (S)  205  and into the integration capacitor (C LOFIC )  204 . 
         [0212]    During the period that the switch means (X)  207  is ON (equivalent to pulse width t 2  of pulse SX 1  and pulse SX 2 ), the pixel combines with the column output line  103  and the following signals are sequentially output. 
         [0213]    When the switch means (SW/AMPEN)  104 HG and the switch means (SW/AMPEN)  104 LG are ON, the gain amplifier  105 HG and the gain amplifier  105 LG are active. 
         [0214]    Before the transfer switch means (T)  202  is turned ON and within the storage time (ST), the switch means (SW/AMPEN)  104 HG and the switch means (SW/AMPEN)  104 LG are turned ON. 
         [0215]    Subsequently, the switch means (NS 1 H)  106 HG- 1  and the switch means (NS 1 )  106 LG- 1  are turned ON and OFF (pulse S HG1  and pulse S LG1 ), the first (1-1) BG signal and the first (1-2) BG signal are each read, and the respective signals are held in the corresponding capacitor (N 1 H)  106 HG- 2  and the capacitor (N 1 )  106 LG- 2 . 
         [0216]    Here, the first (1-1) signal and the first (1-2) signal include signals equivalent to a reset noise (noise signals) of the capacitor (C FD )  203 , a threshold variance of the switch means (SF)  208 , and an offset voltage of the gain amplifier  105 HG and the gain amplifier  105 LG. 
         [0217]    Next, the transfer switch means (T)  202  is turned ON and OFF (pulse ST 2 ), and the charge (also referred to as “photocharge”) that generated inside the PD  201  by light reception is completely transferred to the floating diffusion capacitor (C FD )  203 . 
         [0218]    At this time, when the charge amount of the photocharge is greater than the saturation charge amount of the capacitor (C FD )  203 , the supersaturation amount of the photocharge overflows beyond exceeds the potential of the switch means (S)  205  and into the integration capacitor (C LOFIC )  204 . The photocharge equivalent to the charge amount transferred to the capacitor (C FD )  203  is subjected to charge-voltage conversion in accordance with the capacitance value of the capacitor (C FD )  203 . 
         [0219]    After the transfer switch means (T)  202  is turned OFF (pulse ST 2  OFF), the switch means (SS 1 H)  106 HG- 3  and the switch means (SS 1 )  106 LG- 3  are turned ON and OFF (pulse SHG 3  and pulse SLG 3 ), and the first (1-1) optical signal and the first (1-2) optical signal are respectively read and held in the corresponding capacitor (S 1 H)  106 HG- 4  and the capacitor (S 1 )  106 LG- 4 . This signal reading end timing T 3  is when the switch means (SS 1 H)  106 HG- 3  and the switch means (SS 1 )  106 LG- 3  are OFF. 
         [0220]    Here, in addition to the first (1-1) BG signal and the first (1-2) BG signal, the signal generated in accordance with the charge amount of the photocharge transferred to the capacitor (C FD )  203  is added to the first (1-1) optical signal and the first (1-2) optical signal, and correlation double sampling processing is performed, that is, the first (1-1) BG signal is subtracted from the first (1-1) optical signal and the first (1-2) BG signal is subtracted from the first (1-2) optical signal in a later stage circuit, thereby respectively obtaining only the signals generated in accordance with the charge amount of the photocharge. Naturally, a gain amplifier comprising a correlation double sampling function may be used for the gain amplifiers  105 HG,  105 LG. 
         [0221]    After the first (1-1) optical signal is read to the capacitor (S 1 H)  106 HG- 4  and the first (1-2) optical signal is read to the capacitor (S 1 )  106 LG- 4 , the switch means (SW/AMPEN)  104 HG and the switch means (SW/AMPEN)  104 LG are respectively turned OFF, and the gain amplifiers  105 HG,  105 LG are deactivated. 
         [0222]    Subsequently, the switch means (S)  205  is turned ON, and potentials of the capacitor (C FD )  203  and the integration capacitor (C LOFIC )  204  are combined. 
         [0223]    At this time, when there is a charge that overflows from the capacitor (C FD )  203  and is stored in the integration capacitor (C LOFIC )  204  within the storage time (ST) or within the storage time (ST) and a transfer time (TT), the charge of the charge amount stored in the integration capacitor (C LOFIC )  204  and the charge of the charge amount transferred to and stored in the capacitor (C FD )  203  are mixed together via the switch means (S)  205  and subjected to charge-voltage conversion according to the total capacitance of the integration capacitor (C LOFIC )  204  and the capacitor (C FD )  203 . 
         [0224]    When there is no overflow from the capacitor (C FD )  203  and a charge is not stored in the integration capacitor (C LOFIC )  204 , the charge of the charge amount transferred to the capacitor (C FD )  203  is subjected to charge-voltage conversion according to the total capacitance of the integration capacitor (C LOFIC )  204  and the capacitor (C FD )  203 . 
         [0225]    Here, to transfer to the capacitor (C FD )  203  and the integration capacitor (C LOFIC )  204  the photocharge which is stored in the photodiode (PD)  201  from the moment the transfer switch means (T)  202  is turned OFF by the ON and OFF operation at the pulse ST 2 , an operation of turning the transfer switch means (T)  202  ON and OFF with the switch means (S)  205  ON may be added. 
         [0226]    Subsequently, the switch means (SS 2 )  106 N- 3  is turned ON and OFF (pulse SSS 2 ) within the time (t 1 ) that the switch means (S)  205  is ON, thereby reading and holding the second optical signal in the capacitor (S 2 )  106 N- 4 . The reading end timing at this time is T 4 . 
         [0227]    Next, the switch means (R)  206  is turned ON and the resetting of the integration capacitor (C LOFIC )  204  and the capacitor (C FD )  203  is started. 
         [0228]    Subsequently, the transfer switch means (T)  205  is turned ON and the resetting of the PD  201  is started. 
         [0229]    Next, the switch means (R)  206  is turned OFF and the resetting of the integration capacitor (C LOFIC )  204  and the capacitor (C FD )  203  is ended. 
         [0230]    While reset noise is incorporated into the integration capacitor (CLOFIC)  204  and the capacitor (CFD)  203  at this time, it is possible to remove the reset noise as described previously and make only the signals corresponding to the amount of light received. 
         [0231]    Subsequently, the switch means (NS 2 )  106 N- 1  is turned ON and OFF (pulse S NS22 ), thereby reading and holding the second BG signal in the capacitor (N 2 )  106 N- 2 . 
         [0232]    Subsequently, the switch means (S)  205  is turned OFF, and the potentials of the integration capacitor (C LOFIC )  204  and the capacitor (C FD )  203  are not combined. 
         [0233]    Next, the switch means (X)  207  is turned OFF, the pixel is disconnected from the output line, and the step transitions to the reading time of the pixels of another line. 
         [0234]      FIG. 11  is a flowchart for explaining a procedure when a signal of one pixel is read. 
         [0235]    When imaging is started (step  801 ), the decision is made as to whether or not it is prior to signal output preparation (step  802 ). If it is prior to signal output preparation, the flow transitions to step  803  of acquiring the photoelectric conversion characteristics of the first (1-1) signal  102 S 1 , the first (1-2) signal  102 S 2 , and the second signal  102 N. When the acquisition of the photoelectric conversion characteristics of each signal ends, the flow transitions to step  804 . If, in step  802 , it is not prior to signal output preparation, the flow transitions to step  804 . In step  804 , the decision is made as to whether or not acquisition of the pixel signal has started. When pixel signal acquisition has started, the acquired pixel signal is stored in step  805 . When pixel signal acquisition has not started, the flow returns once again to step  804 , and the decision is made as to whether or not pixel signal acquisition has started. Each signal (first (1-1) signal  102 S 1 , first (1-2) signal  102 S 2 , and second signal  102 N) stored in step  804  is output for transfer to the circuit of the next stage in step  806 . 
         [0236]    Next, the signal indicating the illuminance of the imaging surface is derived from the combination of the outputs of the first (1-1) signal  102 S  1 , the first (1-2) signal  102 S 2 , and the second signal  102 N (step  807 ). Subsequently, the derived signal is output for transfer to a predetermined circuit (step  808 ), and the series of reading operations is ended (step  809 ). 
         [0237]    In the prototype device A according to the present invention, a high-gain amplifier was used for the column circuit portion  102 , making it possible to set the noise voltage of the floating diffusion input conversion to 60 μV. 
         [0238]    When the charge-voltage conversion gain was set to 230 μV/e − , the number of input conversion noise electrons could be set to 0.26, and the signal could be read substantially unproblematically with a per photon accuracy. 
         [0239]    Further, when the charge-voltage conversion gain was set to 300 μV/e − , the number of input conversion noise electrons could be set to 0.20. 
         [0240]    Here, the relationship between the charge-voltage conversion gain and floating diffusion capacitance is given by the formula below. 
         [0000]        CG=q/CFD   (1)
 
         [0241]    “CG” indicates charge-voltage conversion gain, “q” indicates element charge, and “C FD ” indicates floating diffusion capacitance. 
         [0242]    In the trial manufacture of the prototype device A described above, a creation flow in which an n type region (LDD) formed by injecting n type impurities prior to side wall formation of the gate electrode, normally called LDD, is not formed in order to physically minimize overlap between the gate electrode and the n type diffusion layer, is described above, was used. 
         [0243]    Further, after side wall formation, the ion injection step of injecting n type impurities at a high dose of an order of 10 15  cm −2  was changed, decreasing the dose of the n type impurities to 6×10 14  cm −2 , and reducing the concentration of the predetermined n type diffusion layer (n type regions  501 - 1 ,  501 - 2 ,  501 - 3 ). 
         [0244]    As a result, the gate overlap capacitance was further reduced, and a reduction in PN junction capacitance could also be achieved. That is, in the prototype device A, it was possible to set the floating diffusion capacitance to 0.5 fF, the charge-voltage conversion gain to 320 μV/e − , and the number of input conversion noise electrons to 0.19, and read the signal with a one-photon accuracy. Furthermore, the first (1-1) signal, the first (1-2) signal, and the second signal were combined, making it possible to linearly obtain an imaging signal from one electron to 74,000 photons within one exposure period. 
         [0245]    Next,  FIGS. 12 and 13  illustrate an example of a preferred embodiment of a case where the present invention is applied to an imaging device. 
         [0246]      FIG. 12  illustrates an example of a preferred embodiment of a sensor portion of a case where the CMOS image sensor according to the present invention is applied to an imaging device, and is a circuit diagram illustrating N pixel circuits in a first column and one column of reading circuits. 
         [0247]      FIG. 12  illustrates a column pixel circuit portion  1200 - 1  of the first column and a column circuit portion  102 - 1  of the first column. 
         [0248]    In the column pixel circuit portion  1200 - 1 , N pixel (circuit) portions ( 101 - 1  to  101 -N) are arranged as illustrated, and each of the pixel (circuit) portions ( 101 - 1  to  101 -N) is sequentially connected to a pixel column signal line  103 - 1  of the first column. 
         [0249]    While only one column of the column pixel circuit portion is illustrated in  FIG. 12 , M columns are actually arranged ( 1200 - 1  to  1200 -M;  1200 - 2  to  1200 -M are not illustrated). 
         [0250]    A current source  108 - 1 , similar to the case in  FIG. 1 , is connected downstream of the pixel column signal line  103 - 1 . 
         [0251]    The column circuit portion  102 - 1 , similar to the case in  FIG. 1 , comprises a first column reading circuit  102 HG- 1  provided with a high-gain amplifier, a second column reading circuit  102 LG- 1  provided with a low-gain amplifier, and the third column reading circuit  102 N. 
         [0252]    Further, each of the column reading circuits ( 102 HG- 1 ,  102 LG- 1 ,  102 N), similar to the case in  FIG. 1 , is provided with an analog memory circuit portion. 
         [0253]    The method for reading the signal in the case in  FIG. 12  is the same as that previously described except reading is repeated for N rows. 
         [0254]      FIG. 13  is an overall block diagram schematically illustrating the entire sensor portion of the example of the imaging device illustrated in  FIG. 12 . 
         [0255]    A sensor portion  1300  comprises a pixel array  1301  provided with “N×M” pixels comprising the pixel circuit portion (equivalent to one pixel)  101  illustrated in  FIG. 1  arranged two dimensionally therein, a vertical (row) shift register portion  1302 , and a horizontal (column) shift register portion  1303 . 
         [0256]    In the row direction of the pixel array  1301 , the sensor portion  1300  comprises a current source column portion  1304  with M current sources  108  arranged therein, a reset switch column portion  1305  with M pixel output line reset switch means arranged therein, a first (1-1) signal analog memory portion  1307  with M analog memory circuit portions  106 HG arranged therein, a first (1-2) signal analog memory portion  1309  with M analog memory circuit portions  106 LG arranged therein, and a second signal analog memory portion  1310  with M analog memory circuit portions  106 N arranged therein. 
         [0257]    A 16× amplifier column portion  1306  is provided between the column reset switch portion  1305  and the first (1-1) signal analog memory portion  1307 , and a Ix amplifier column portion  1308  is provided between the first (1-1) signal analog memory portion  1307  and the second signal analog memory portion  1310 . 
         [0258]    Here, the 16× amplifier column portion  1306  means that an amplifier having a 16× amplification factor is used as the high-gain amplifier, and the 1× amplifier column portion  1308  means that an amplifier having a 1× amplification factor is used as the low-gain amplifier. 
         [0259]    A final stage buffer  1311  is a buffer for outputting the holding signal of analog memory of columns sequentially selected by a horizontal shift register to an area outside the chip using low output impedance. 
         [0260]    Next, an example of an optimum design of the optical sensor of the present invention will be described. 
         [0261]      FIGS. 14 to 16  are diagrams illustrating a schematic layout pattern of the pixel selection switch means (X)  207  and the source follower switch means (SF)  208 . 
         [0000]    (1) The gate overlap capacitance on the source follower gate drain side, which is a component of the floating diffusion capacitor, is proportional to the width (W SF   _   D ) on the source follower gate drain side, and thus the width of the source follower gate is preferably small. 
         [0262]      FIG. 14  is a preferred example of a layout pattern that prioritizes minimizing the width of the source follower gate to reduce the overlap capacitance. 
         [0263]    W SF   _   D  is preferably designed with the smallest machining dimensions, and is set to 0.34 μm in the preferred specific example of the present invention. 
         [0000]    (2) To increase the gain of the source follower circuit and reduce the low frequency noise consisting of I/F noise and random telegraph noise, the gate width of the source follower gate is preferably increased. 
         [0264]      FIG. 15  is a preferred example of a layout pattern that prioritizes increasing the width of the source follower gate to increase the gain of the source follower circuit and reduce low frequency noise. 
         [0265]    In the preferred specific example of the present invention, both W SF   _   S  and W SF   _   D  are set to 0.60 μm. 
         [0000]    (3)  FIG. 16  illustrates an example in which active Si is asymmetrically arranged in a channel region that covers gate polysilicon and active Si (offering the advantage of applying asymmetrically shaped active Si to the source follower gate). 
         [0266]    When the active Si width is widened from W SF   _   D  to W SF   _   S  and an asymmetrical shape is formed, preferably the current path is gently widened, thereby laying out the active Si at a gentle angle with the direction of flow of the current that runs directly in the gate width direction serving as standard so that carrier scattering decreases. 
         [0267]    In the preferred specific example of the present invention, the active Si is laid out at an incline of ±45° with the direction of current flow serving as standard. 
         [0268]    Further, while deviation from design values occurs in the gate polysilicon and the active Si due to photolithography misalignment, a margin must be provided to ensure that the W SF   _   D  and W SF   _   S  values do not fluctuate even if misalignment occurs. Here, the designable range of W SF   _   S  is given by formula (2) below. 
         [0000]        W   SF   _   D   ≦W   SF   _   S   ≦W   SF   _   D +2· L   SF −2· L   M )   Formula (2)
 
         [0269]    Here, L M  is the minimum value of the misalignment margin. 
         [0270]    In  FIG. 16 , L M  is indicated by L M1 , L M2 . 
         [0271]    In the preferred specific example of the present invention, L M  (L M1 , L M2 )=0.10 μm. 
         [0272]    W SF   _   D  is preferably designed using the smallest machining dimensions. 
         [0273]    In the preferred specific example of the present invention, W SF   _   D  is set to 0.34 μm. Further, L SF  is set to 0.55 μm. Thus, the maximum designable W SF   _   S  value at this time is 1.04 μm. 
         [0274]    In the preferred specific example of the present invention, W SF   _   S  is set to 0.60 μm. 
         [0275]    In the present invention, the layout is designed so as to satisfy the above conditions (1) to (3), making optimization possible. 
         [0276]    In the most preferred example, the active Si is asymmetrically arranged and the gate width (W SF   _   D ) on the drain side is minimized to reduce the gate overlap capacitance, and the gate width (W SF   _   S ) on the source side is increased, making it possible to achieve both an increase in gain of the source follower circuit and a reduction in low frequency noise. 
       DESCRIPTIONS OF REFERENCE NUMERALS 
       [0000]    
       
           100 : Pixel circuit and one column of reading circuits 
           101 : Pixel circuit portion 
           101 - 1  to  101 -N: Pixel portion 
           102 ,  102 - 1 : Column circuit portion 
           102 HG,  102 HG- 1 : First column reading circuit 
           102 LG,  102 LG- 1 : Second column reading circuit 
           102 N,  102 N- 1 : Third column reading circuit 
           102 S 1 : First (1-1) signal 
           102 S 2 : First (1-2) signal 
           102 SN: Second signal 
           103 ,  103 - 1 : Pixel column output signal line 
           104 HG: Switch means (SW/AMPEN) 
           104 LG: Switch means (SW/AMPEN) 
           105 HG: High-gain amplifier 
           105 LG: Low-gain amplifier 
           106 HG: Analog memory circuit portion 
           106 LG: Analog memory circuit portion 
           106 N: Analog memory circuit portion 
           106 HG- 1 : Switch means (NS 1 H) 
           106 LG- 1 : Switch means (NS 1 ) 
           106 N- 1 : Switch means (NS 2 ) 
           106 HG- 2 : Capacitor (N 1 H) 
           106 LG- 2 : Capacitor (N 1 ) 
           106 N- 2 : Capacitor (N 2 ) 
           106 HG- 3 : Switch means (SS 1 H) 
           106 LG- 3 : Switch means (SS 1 ) 
           106 N- 3 : Switch means (SS 2 ) 
           106 HG- 4 : Capacitor (S 1 H) 
           106 LG- 4 : Capacitor (S 1 ) 
           106 N- 4 : Capacitor (S 2 ) 
           107 HG: Signal line for first (1-1) signal 
           107 LG: Signal line for first (1-2) signal 
           107 N 1 : Signal line for second signal from pixel column output signal line 
           108 ,  108 - 1 : Current source 
           201 : Photodiode (PD) 
           202 : Transfer switch means (T) 
           202 - 1 : Electrode of transfer switch means (T) 
           203 : Floating diffusion capacitor (C FD ) 
           204 : Lateral overflow integration capacitor (C LOFIC ) 
           205 : Overflow switch means (S) 
           205 - 1 : Electrode of overflow switch means (S) 
           206 : Reset switch means (R) 
           206 - 1 : Electrode of reset switch means (R) 
           207 : Pixel selection switch means (X) 
           207 - 1 : Electrode of pixel selection switch means (X) 
           208 : Source follower switch means (SF) 
           208 - 1 : Electrode of source follower switch means (SF) 
           300 : p −  type epi substrate 
           301 A 1 ,  301 A 2 ,  301 B 1 ,  301 B 2 : MOS transistor 
           302 : Diffusion layer (n; type region) 
           303 A,  303 B: Gate electrode 
           304 A,  30481 ,  304 B 2 : Side wall 
           305 : LDD. 
           306 : Insulation film layer 
           400 : p −  type epi substrate 
           401 A 1 ,  401 A 2 : MOS transistor 
           402 A: Diffusion layer (n +  type region) 
           403 A,  403 B: Gate electrode 
           404 A,  404 B 1 ,  403 B 2 : Side wall 
           500 : Optical input sensor pixel portion 
           500 - 1 : n −  type silicon (n − Si) substrate 
           500 - 2 : p type silicon layer 
           501 - 1  to  501 - 3 : Impurity reduction n type region 
           502 - 1  to  502 - 5 : n +  type region 
           503 - 1  to  503 - 6 : LDD 
           504 : FD diffusion layer portion 
           505 : Pixel SF portion 
           506 - 1  to  506 - 4 : Element isolation region 
           507 - 1  to  507 - 3 : p type embedded region 
           508 : n −  type region 
           509 : p +  type region 
           510 : STI periphery p +  type region 
           601 - 1  to  601 - 3 : LDD formation photoresist 
           602 - 1  to  602 - 11 : Side wall 
           603 - 1  to  603 - 2 : S/D diffusion layer formation photoresist 
           604 - 1  to  604 - 3 : S/D high concentration diffusion layer formation photoresist 
           605 - 1  to  605 - 2 : Wiring interlayer insulator layer 
           606 - 1  to  606 - 3 : Contact electrode 
           607 - 1  to  607 - 2 : Metal wiring 
           801  to  809 : Signal reading step 
           1200 - 1 : Column circuit portion of first column 
           1300 : Sensor portion 
           1301 : Pixel array 
           1302 : Vertical shift resistor 
           1303 : Horizontal shift resistor 
           1304 : Current source column portion 
           1305 : Pixel output line reset switch column portion 
           1306 : 16× amplifier portion 
           1307 : First (1-1) signal analog memory portion 
           1308 : 1× amplifier column portion 
           1309 : First (1-2) signal analog memory portion 
           1310 : Second signal analog memory portion 
           1311 : Final stage buffer