Abstract:
An input signal with an associated pulse width can be sampled using a sampling method that does not require a clock signal. The input signal is compared to a reference level signal to produce a comparator output signal. Strobe signals are generated from the input signal, where the strobe signals occur within a pulse width of the input signal. Sampled data points are generated in response to the comparator output signal and the strobe signals such that the sampled data points are within the pulse-width of the input signal. One of the strobe signals may be used to periodically reset the comparator. The sampling logic circuit may be constructed from common logic gates and memory circuits such as flip-flops. In one example application the sampling method is applied to an equalizer system. The equalizer system includes an equalizer circuit that produces an equalized signal. A data slicer circuit converts the equalized signal into a digital representation. The sampling method is applied to the output of the data slicer circuit to generate the sampled data points in the equalizer system. The sampled data points may be used in the equalizer system or any other system that requires samples of the input signal without the use of a clock signal. Since the sampling system uses the incoming data signal to generate the requisite timing signals for sampling, high frequency clock circuits and phase locked loop techniques are unnecessary resulting in lower power consumption and reduced costs.

Description:
FIELD OF THE INVENTION 
   The present invention relates to a method and apparatus for sampling an input signal without the use of a clock signal. In particular, the present invention relates to a method and apparatus that generates timing signals from the input signal. The timing signals are used by a sampling circuit that produces sampled data points that correspond to samples from the input signal. The present invention may be used in a system such as an equalizer system that receives a data signal, samples the data signal and adjusts the equalization levels based on the sampled data. 
   BACKGROUND OF THE INVENTION 
   Data signals are degraded when transmitted over long lengths of cable. As the frequency of the data signal increases, the adverse effects on signal quality become more prevalent in the received signal. The data signal will become degraded in amplitude due to loss and phase dispersion from the cable. 
   Digital data signals consist of an infinite series of frequency components. High frequency digital data signals have very fast edges resulting in larger amplitudes in the high frequency components of the signal. Since the loss in the cable increases with frequency, the higher frequency components in fast edge digital data signals become greatly attenuated over distance when compared to the lower frequency components. 
   Equalization systems attempt to correct for high frequency losses and signal dispersion over cabling by boosting the higher frequency components of received data signals. High pass filters are used as equalizers to balance the frequency components of the received signal and attempt to reconstruct the fast edges found in the original data signal. The cable can be represented as a transfer function between the original signal and the received signal. By designing the high pass filter to have the inverse transform function of the cable&#39;s characteristics, the adverse effects of the cable loss can be eliminated. 
   The high pass equalization method may be represented as a simple capacitor and resistor network. Since the data signal is effectively AC coupled through the filter, a DC restore circuit is often required to recover a DC baseline for the incoming signal. DC servo circuits are often employed for this purpose. Once a proper DC level has been restored to the equalized signal, the data signal can be detected through a comparator circuit. The comparator and the DC restore circuit may be combined into a single circuit such as through the use of positive feedback from the output of the comparator. The output of such a comparator is a “sliced” version of the received data signal. 
   Phase locked loop and delay locked loop techniques may be used to provide adaptive equalization. The sliced data signal can be combined in a phase locked loop to adjust the high pass filter such that the transform function of the high pass filter closely matches the inverse transform of the cable. 
   SUMMARY OF THE INVENTION 
   In accordance with the present invention, a sampling system and method samples data points from an input signal without the use of a clock signal. The overall system operates at high speeds without the use of phase-locked loops and other complex methodologies, reducing cost and power consumption. 
   Briefly stated, the present invention relates to a sampling method that samples data points from an input signal that has an associated pulse-width, without the use of a clock signal. The input signal is compared to a reference level signal to produce a comparator output signal. Strobe signals are generated from the input signal, where the strobe signals occur within a pulse width of the input signal. Sampled data points are generated in response to the comparator output signal and the strobe signals such that the sampled data points are within the pulse-width of the input signal. One of the strobe signals may be used to periodically reset the comparator. The sampling logic circuit may be constructed from common logic gates and memory circuits such as flip-flops. In one example application the sampling method is applied to an equalizer system. The equalizer system includes an equalizer circuit that produces an equalized signal. A data slicer circuit converts the equalized signal into a digital representation. The sampling method is applied to the output of the data slicer circuit to generate the sampled data points in the equalizer system. The sampled data points may be used in the equalizer system or any other system that requires samples of the input signal without the use of a clock signal. Since the sampling system uses the incoming data signal to generate the requisite timing signals for sampling, high frequency clock circuits and phase locked loop techniques are unnecessary resulting in lower power consumption and reduced costs. 
   In accordance with a feature of the invention, a clock free apparatus samples an input signal that has a pulse-width defined between a first edge and a second edge. The apparatus includes a timing delay circuit that is arranged to produce strobe signals in response to the input signal such that the strobe signals have pulse-widths that are within the pulse-width of the input signal. A comparator circuit is arranged to produce a comparator output signal in response to a comparison between the input signal and a reference level signal. A sampling logic is arranged to sample data points within a sampling window in response to the strobe signals and the comparator output signal, the sampling window having edges that correspond to the pulse-width of the input signal such that the sampled data points correspond to samples from the comparator output signal. 
   In accordance with another feature of the invention, a method is directed to clock free sampling of an input signal that has a pulse-width defined between a first edge and a second edge. The method includes comparing the input signal to a peak level signal to produce a comparator output signal, generating a first and second timing signal from the input signal, wherein the first and second timing signals are within the pulse-width of the input signal, sampling a first data point from the comparator output in response to the comparator output signal, and sampling a second data point from the comparator output in response to a second timing signal, wherein the first and second data points correspond to sample points that are within the pulse-width of the input signal. 
   In accordance with yet another feature of the invention, an apparatus is directed to a clock free system for sampling an input signal that has a pulse-width defined between a first edge and a second edge. The system includes a means for producing data produces a data signal in response to the input signal, the data signal corresponding to a digital representation of the input signal. A means for producing a first timing signal produces a first timing signal in response to the data signal, wherein the first timing signal is a pulse that occurs a first time delay after a change in the data signal between a logic state and another logic state. A means for producing a second timing signal produces a second timing signal in response to the data signal, wherein the second timing signal is a pulse that occurs a second time delay after the data signal changes from the logic state to the other logic state, and the pulses of the first timing signal and the second timing signal are within the pulse-width of the input signal. A means for comparing produces a comparator output signal in response to a comparison between the input signal and a reference level signal. A means for sampling data points produces a first sampled data point in response the comparator output signal and the first and second strobe signals, the means for sampling also produces a second sampled data point in response to the comparator output signal and at least one of the first and second strobe signals, wherein the first and second sampled data points correspond to sampled data points within the pulse-width of the input signal. 
   Additionally, a means for analyzing determines a condition of the input signal by analyzing the first sample point and the second sample point. A means for determining persistence determines when the condition of the input signal becomes a persistent condition. The condition of the input signal may be an over-amplitude condition, an under-amplitude condition, an over-shoot condition, and an under-shoot condition. The condition of the input signal is persistent when the condition has continued for a predetermined number of consecutive occurrences. Furthermore, a means for increasing an equalization level that increases the equalization level of the means for equalizing when the under-shoot condition is persistent, and a means for decreasing the equalization level that decreases the equalization level of the means for equalizing when the over-shoot condition is persistent. A means for increasing the peak level signal may be employed to increase the peak level signal when the under-amplitude condition is persistent, while a means for decreasing the peak level signal may be employed to decrease the peak level signal when the over-amplitude condition is the persistent condition. 
   A more complete appreciation of the present invention and its improvements can be obtained by reference to the accompanying drawings, which are briefly summarized below, to the following detail description of presently preferred embodiments of the invention, and to the appended claims. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
       FIG. 1  is a schematic diagram of a sampling system; 
       FIG. 2  is a schematic diagram of another sampling system; 
       FIG. 3  is a graph of waveforms related to an over-equalized signal; 
       FIG. 4  is a graph of waveforms related to an under-equalized signal; 
       FIG. 5  is a graph of waveforms related to an over-amplitude adjusted signal; 
       FIG. 6  is a graph of waveforms related to an under-amplitude adjusted signal; 
       FIG. 7  is a schematic of sampling logic in an equalization system; 
       FIG. 8  is a graph of waveforms related to the sampling logic shown in  FIG. 7 ; and 
       FIG. 9  is another graph of waveforms related to the sampling logic shown in  FIG. 7 , in accordance with the present invention. 
   

   DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT 
   Throughout the specification, and in the claims, the term “connected” means a direct electrical connection between the things that are connected, without any intermediary devices. The term “coupled” means either a direct electrical connection between the things that are connected, or an indirect connection through one or more passive or active intermediary devices. The term “circuit” means one or more passive and/or active components that are arranged to cooperate with one another to provide a desired function. The term “signal” means at least one current signal, voltage signal or data signal. 
   The present invention relates to a data receiver that receives an input signal and produces sampled data points from the received input signal. A reference level generator (or generators) produces a reference level (or levels). A comparator is used to compare a received input signal with the reference level. The output of the comparator is used to generate sample data points from the received/equalized input signal. The sample data points correspond to data points that are sampled from the input signal. 
     FIG. 1  shows a schematic of an exemplary sampling system that is in accordance with the present invention. As shown in the figure, the system includes an equalizer ( 110 ), a data slicer ( 120 ), a timing delay ( 130 ), a reference generator ( 140 ), a comparator ( 150 ), and a sampling logic ( 160 ). 
   The equalizer ( 110 ) includes an input terminal (IN) and an output terminal (OUT). The equalizer receives a data signal (DATAIN) through the input terminal (IN). The equalizer produces an output signal (EQOUT,  112 ) through the output terminal (OUT). The equalizer ( 110 ) may optionally be controlled by a control signal (not shown) to vary the shape of the differential output signal (EQLO, EQHO). The shape of the output signal (EQOUT,  112 ) corresponds to a shaped version of the data signal (DATAIN). 
   The data slicer ( 120 ) includes an input terminal (IN) and an output terminal (OUT). The input terminal (IN) of the data slicer ( 120 ) receives the output of the equalizer (EQOUT,  112 ), and couples an output signal (DSOUT,  122 ) to the output terminal (OUT) of the data slicer ( 120 ). The output (DSOUT,  122 ) of the data slicer ( 120 ) corresponds to data that is extracted from the output signal of the equalizer (EQOUT,  112 ). 
   The timing delay ( 130 ) includes an input terminal (IN) and an output terminal (OUT). The input terminal (IN) of the timing delay ( 130 ) receives the output of the data slicer (DSOUT,  122 ). The timing delay ( 130 ) produces one or more timing signals that are coupled to the output terminal (OUT) of the timing delay ( 130 ) as DLYOUT ( 132 ). The timing signal (DLYOUT) or signals are used as strobe signals for sampling in other circuits. 
   The reference generator ( 140 ) produces an output signal (REF_LVL,  142 ) through an output terminal (OUT). The reference level (REF_LVL) may optionally be adjusted by a control signal (not shown). 
   The comparator ( 150 ) includes two input signal terminals (IN 1 , IN 2 ), a reset control terminal (RST), and an output terminal (OUT). The first input signal terminal (IN 1 ) receives the output signal (EQOUT,  112 ) from the equalizer ( 110 ). The second input signal terminal (IN 2 ) receives the output signal (REF_LVL,  142 ) from the reference level generator ( 140 ). The reset control terminal (RST) receives the output signal (DLYOUT,  132 ) from the timing delay ( 130 ). The comparator ( 150 ) produces an output signal (CPOUT,  152 ) through its corresponding output terminal (OUT). When the reset control terminal is not active (RST not active), the comparator output signal (CPOUT,  152 ) corresponds to a comparison between the EQOUT signal ( 112 ) and the REF_LVL signal ( 142 ). 
   The sampling logic includes two input terminals (IN 1 , IN 2 ) and an output terminal (DOUT). One of the input terminals (IN 1 ) receives the output signal (DLYOUT,  132 ) from the timing delay ( 130 ). The other of the input terminals (IN 2 ) receives the output signal (CPOUT,  152 ) from the comparator ( 150 ). The sampling logic produces sampled data points (SAMPLE DATA) in response to the input signals (DLYOUT, CPOUT). 
     FIG. 2  shows another example schematic of an exemplary sampling system that is in accordance with the present invention. As shown in the figure, the system includes an equalizer ( 210 ), a data slicer ( 220 ), a timing delay ( 230 ), a top peak generator ( 240 ), a bottom peak generator ( 244 ), a comparator ( 250 ), and a sampling logic ( 260 ). 
   The equalizer ( 210 ) includes a pair of input terminals (INH, INL), and a pair of output terminals (OUTH, OUTL). The equalizer receives a differential data signal (DATA+, DATA−) through the input terminals (INH, INL). The equalizer produces a differential output signal (EQHO, EQLO) through the output terminals (OUTH, OUTL). The equalizer may optionally be controlled by a control signal (not shown) to vary the shape of the differential output signal (EQLO, EQHO). The shape of the differential output signal (EQHO, EQLO) corresponds to a shaped version of the differential data signal (DATA+, DATA−). 
   The data slicer ( 220 ) includes a pair of input terminals (INH, INL) and an output terminal (OUT). The input terminals (INH, INL) of the data slicer ( 220 ) receive the output signals (EQHO, EQLO) from the equalizer ( 210 ), and couples an output signal (DSOUT,  222 ) to the output terminal (OUT) of the data slicer ( 220 ). The output (DSOUT,  222 ) of the data slicer ( 220 ) corresponds to data that is extracted from the output differential signal (EQHO, EQLO) of the equalizer ( 210 ). 
   The timing delay ( 230 ) includes an input terminal (IN) and a pair of output terminals (T2_SIG, T3_SIG). The input terminal (IN) of the timing delay ( 230 ) receives the output of the data slicer (DSOUT,  222 ). The timing delay ( 230 ) produces one or more timing signals that are coupled to the output terminals of the timing delay ( 230 ) as T2_SIG ( 234 ) and T3_SIG ( 232 ). The timing signals (T2_SIG, T3_SIG) are used as strobes signals in the sampling circuit ( 260 ). 
   The top peak generator ( 240 ) is arranged to provide a top peak level (TPO,  242 ) through an output terminal (OUT). The bottom peak generator ( 244 ) is arranged to provide a bottom peak level (BPO,  246 ) through an output terminal (OUT). The top peak level (TPO) may optionally be adjusted by a top peak control signal (not shown). The bottom peak level (TPO) may optionally be adjusted by a bottom peak control signal (not shown). 
   The comparator ( 250 ) includes four input signal terminals (INH 1 , INH 2 , INL 1 , INL 2 ), a reset control terminal (RST), and an output terminal (OUT). The first input signal terminal (INH 1 ) receives the top output signal (EQHO,  212 ) from the equalizer ( 210 ). The second input signal terminal (INH 2 ) receives the output signal (TPO,  242 ) from the top peak generator ( 240 ). The third input signal terminal (INL 1 ) receives the bottom output signal (EQLO,  214 ) from the equalizer ( 210 ). The fourth input signal terminal (INL 2 ) receives the output signal (BPO,  246 ) from the bottom peak generator ( 244 ). The reset control terminal (RST) receives the output signal (T2_SIG,  234 ) from the timing delay ( 230 ). The comparator ( 250 ) produces an output signal (CPOUT,  252 ) through its corresponding output terminal (OUT). When the reset control terminal is not active (RST not active), the comparator block ( 250 ) outputs a signal (CPOUT) corresponding to the comparison of the differential equalized signal (EQHO, EQLO) and the differential amplitude levels (TPO, BPO). 
   The sampling control logic ( 260 ) includes three input terminals (T2_SIG, T3_SIG, INCP), and two output terminals (SP 1 , SP 3 ). The T2_SIG and T3_SIG input terminals receive the T2_SIG output signal ( 234 ) and the T3_SIG output signal ( 232 ) from the timing delay ( 230 ). The INCP input terminal receives the output signal (CPOUT,  252 ) from the comparator ( 250 ). The digital control logic produces control signals in response to the input signals (T2_SIG, T3_SIG, CPOUT). 
   As shown in  FIGS. 1 and 2 , equalization is performed on an incoming signal. Equalization is performed to compensate for loss of amplitude, shift in phase, as well as other effects such as noise on the incoming signal. The sampling logic shown in  FIGS. 1 and 2  sample the equalized signal to generate sample points (T1_SP 1 , T3_SP 1 ). The sample points may be analyzed to determine any amount of undershoot, overshoot, over-amplitude, and under-amplitude that occurs in the output of the equalizer. Other circuitry (not shown) may be utilized to adjust the equalizer for optimal performance. The other circuitry may analyze the sampled data points from the output of the equalizer to determine the condition of the equalized data-signal (i.e. undershoot, overshoot, etc.). 
   Two points may be sampled from the equalizer output to determine the condition of the equalized data-signal.  FIGS. 3-6  illustrate exemplary equalized signals (i.e. EQOUT  112  in FIG.  1 ), and corresponding output signals from the comparator (i.e. CPOUT  152  in FIG.  1 ).  FIGS. 3-6  include an ideal data signal shown as a voltage waveform that varies over time. Sample points P 1  and P 2  are evaluation points for the comparator at times T1 and T3 respectively. The comparator outputs follow after the comparisons are made at times T1 and T3. For simplicity, changes in the output of the comparator will simply be referred to as “at time T1” or “at time T3”. 
     FIG. 3  illustrates an equalized signal that has excessive amounts of overshoot (over-equalized). The output of the equalizer overshoots the top peak level as shown by sample point P 1  at time T1. At time T3, the signal drops to a level below the top peak level as shown by sample point P 2 . The comparator output level at time T1 is a high logic level, while the comparator output level at time T3 is a low logic level. Overshoot may be caused by excessive amounts of gain in the equalizer as well as other causes that are known to one of ordinary skill in the art having read the above discussion. 
     FIG. 4  illustrates an equalized signal that is under-equalized as shown by excessive amounts of undershoot. The output of the equalizer undershoots (does not reach) the top peak level as shown by sample point P 1  at time T1. At time T3, the signal exceeds the top peak level as shown by sample point P 2 . The comparator output level at time T1 is a low logic level, while the comparator output level at time T3 is a high logic level. Undershoot may be caused by insufficient amounts of gain in the equalizer as well as other causes that are known to one of ordinary skill in the art having read the above discussion. 
     FIG. 5  illustrates an equalized signal that has excessive amounts of amplitude (over-amplitude). The output of the equalizer exceeds the top peak level at times T1 and T3 as shown by sample points P 1  and P 2 . The comparator will output a high logic levels at times T1 and T3. In this instance, the peak levels may be appropriately adjusted for maximum signal size. 
     FIG. 6  illustrates an equalized signal that has insufficient amplitude levels (under-amplitude). The output of the equalizer fails to exceed the top peak level at times T1 and T3 as shown by sample points P 1  and P 2 . The comparator will output a low logic levels at times T1 and T3. As with case of over-amplitude signals, the peak levels should be appropriately adjusted for maximum signal size. 
   The data slicer shown in  FIGS. 1 and 2  operate similar to a comparator that converts an analog waveform into a digital waveform. The data slicer receives a signal from the output of the equalizer and outputs a signal that has the same duty cycle and distortion of the equalized signal in digital form. The data slicer can be designed using comparators, inverters, as well as other combinations of analog and digital electronic devices that are configured to convert an analog signal to a digital logic signal. In one example of the present invention, the data slicer receives a differential analog signal and converts the differential analog signal to a differential digital signal. In another example of the present invention, the data slicer receives a differential analog signal and converts the differential analog signal to a single ended digital signal. In light of the above discussion, other arrangements for the data slicer are possible without departing from the scope of the invention. 
   The timing delay block produces strobe signals that are used by the sampling control logic and the comparator. As shown in  FIG. 2 , two strobe signals (T2_SIG and T3_SIG) are generated by the timing delay cell ( 230 ). The strobe signals are used to sample data from the equalized signal as described with reference to  FIGS. 3-6 . In one embodiment of the present invention, the frequency of the T3_SIG strobe signal is approximately the same as the output signal from the data slicer, and the frequency of the T2_SIG signal is approximately twice that of the output signal from the data slicer. The pulse-widths of the T2_SIG and T3_SIG signals are fixed widths that are narrower than the incoming signal pulse-width. The pulse-widths of the T2_SIG and T3_SIG signals need not be the same as one another. 
   The T2_SIG pulse occurs a fixed interval after the data signal changes from one logic level to another. In one embodiment, the T2_SIG pulses low for a fixed interval after the output signal from the data slicer changes logic states. The T2_SIG pulse can be generated by various methods including but not limited to combinational logic combined with skewed inverter/delay circuits. The T3_SIG pulse is generated in a similar way as T2_SIG. In one embodiment, the T3_SIG signal pulses from a logic low to a logic high a time interval after the output signal from the data slicer changes from a high logic level to a low logic level. 
   The comparator block receives a periodic reset pulse from the T2_SIG signal of the timing delay block. In one example, the comparator output is reset to a low logic level after receiving a low logic level reset pulse. While the reset pulse is inactive (high logic level), the comparator compares the input signals to the comparator and provides a logic output corresponding to the comparison. In one example, the inputs to the comparator (e.g., EQOUT and REF_LVL) are single ended logic signals such as shown in FIG.  1 . In another example, the inputs to the comparator (e.g. EQHO, EQLO and TPO, BPO) are differential signals and the comparator performs a differential comparison to determine the output logic signal such as shown in FIG.  2 . 
   In accordance with the present invention, an exemplary sampling logic block is shown in FIG.  7 . The sampling logic block uses the timing signals (e.g., T2_SIG and T3_SIG) signals together with the output signal from the comparator (COMP_OUT) to generate sample data points (T1_SP 1 , T3_SP 1 ). The exemplary sampling logic includes four flip-flop circuits ( 710 - 740 ), each having a D input, a clock input, a reset input (RST), and Q and NQ output terminals. The sampling logic also includes an inverter (INV 1 ) and a logical OR gate (OR 1 ) to generate signals for controlling the flip-flops ( 710 - 740 ). The first inverter (INV 1 ) produces a first signal ( 702 , T2B) from a first timing signal (T2_SIG). The logical OR gate (OR 1 ) produces another reset signal ( 706 , RST) from the reset signal (RESET) and a second timing signal (T3_SIG). 
   The first flip-flop ( 710 ) is arranged with a data signal (COMP_OUT) coupled to the clock input, the NQ output ( 712 ) is coupled to the D input, and the RST input is coupled to a first reset signal ( 706 , RS 1 ). The Q output ( 714 ) from the first flip-flop ( 710 ) is coupled to the D input of the second flip-flop ( 720 ). The second flip-flop ( 720 ) is arranged with an inverted version of the T2_SIG timing signal ( 702 , T2B) coupled to the clock input, and the reset signal (RST) is coupled to the reset signal (RESET). The Q output ( 724 ) from the second flip-flop ( 720 ) is coupled to the D input of the third flip-flop ( 730 ). The third flip-flop ( 730 ) is arranged with the second reset signal (RST) coupled to the reset signal (RESET), and the second timing signal (T3_SIG) is coupled to the clock input. The Q output (T1_SP 1 ) of the third flip-flop ( 730 ) serves as an output signal corresponding to the first sample point discussed previously. The fourth flip-flop ( 740 ) is arranged with the data signal (COMP_OUT) coupled to the D input, the second timing signal (T3_SIG) coupled to the clock input, and the reset signal (RESET) coupled to the RST input. The Q output (T3_SP 1 ) of the fourth flip-flop ( 740 ) serves as an output signal corresponding to the second sample point discussed previously. The data signal (COMP_OUT) shown in  FIG. 7  corresponds to an output from a comparator such as the comparators shown in  FIGS. 1 and 2 . 
   The first flip-flop ( 710 ) is used to sample the first data point from the incoming signal. The second flip-flop ( 720 ) is used to store the first sampling point so that the first flip-flop ( 710 ) can be reset by the second timing signal (T3_SIG). The third flip-flop ( 730 ) is used to synchronize the first sampling point with the second timing signal (T3_SIG) so that the first and second sampling points appear at their respective outputs (T1_SP 1 , T3_SP 1 ) at the same time. The fourth flip-flop ( 740 ) is used to sample the second sampling point. 
   The RESET signal is held at a high logic level in order to initialize the sampling circuit. The RST will be a high logic level during initialization, causing all four flip-flops ( 710 - 740 ) to be reset such that the Q outputs are reset to a low logic level. In one example of the present invention, the RESET signal pulses high when it is desired to initialize the logic under a power-on-reset condition. In another example, the RESET signal pulses high periodically to reinitialize the equalizer and amplitude adjustments. The operation of the circuit shown in  FIG. 7  will proceed under normal operation after the RESET signal changes to a low logic level. 
   During normal operation, the output of the comparator (COMP_OUT) is used to clock the first flip-flop ( 710 ). By using the comparator output to clock the flip-flop, the first sampling point is as close as possible to the transition of the incoming data. After initialization (flip-flops are reset), the first transition from low to high in the incoming signal (COMP_OUT) will cause the Q output ( 714 ) of the first flip-flop ( 710 ) to change from a low logic level to a high logic level. The operation of the flip-flops ( 710 - 740 ) will now be discussed with reference to  FIGS. 8-9 . 
   In  FIG. 8 , the output of the equalizer is higher than the top peak level at times T1, T2 and T3. Initially, all of the flip-flops ( 710 - 740 ) are reset causing the Q outputs ( 714 ,  724 , T1_SP 1 , T3_SP 1 ) to set to a low logic level. At time T1, the comparator output (COMP_OUT) transitions from low to high causing the first flip-flop ( 710 ) to set the Q output ( 714 ) to a logic high signal. A short time after the transition of the equalizer output signal (at time T2), the timing signal T2_SIG pulses from high to low, causing the second flip-flop ( 720 ) to latch the first sampled data point ( 714 ) to the Q output ( 724 ). At time T3 the equalizer output change from a high level to a low level and the T3_SIG timing signal pulses from low to high for a fixed time interval. The T3_SIG pulse causes the first flip-flop ( 710 ) to reset the output ( 714 ) to a low logic level, and the Q output ( 724 ) of the second flip-flop ( 720 ) is latched into the Q output (T1_SP 1 ) of the third flip-flop ( 730 ). At the same time the T3_SIG pulse causes the fourth flip-flop to latch the comparator output (which is still high) into the Q output (T3_SP 1 ) of the fourth flip-flop ( 740 ). A short time after the equalizer output transitions from a high level to a low level, the T2_SIG timing signal will pulse low again, causing the second flip flop ( 720 ) to set the Q output ( 724 ) to a low logic level, and simultaneously resetting the comparator output to a low logic level. 
   In  FIG. 8 , both points P 1  and P 2  of the Equalizer Output signal are above the top peak level. By using the sampling circuit previously described, sample points T1_SP 1  and T3_SP 1  both correspond to a logic high level at time T3. Thus, sample points T1_SP 1  and T3_SP 1  match with the fact that Equalizer Output signal is above the top peak level at both times T1 and T3. In other words, the sampling circuit functions as a means of translating the condition of the equalized data signal to a logic high or low as reflected by sampling points T1_SP 1  and T3_SP 1 . Sampling points T1_SP 1  and T3_SP 1  may be used to determine if a particular condition occurs. 
   In  FIG. 9 , the output of the equalizer (Equalizer Output) is higher than the top peak level at time T1, and lower than the top peak at times T2 and T3. Initially, all of the flip-flops ( 710 - 740 ) are reset causing the Q outputs ( 714 ,  724 , T1_SP 1 , T3_SP 1 ) to set to a low logic level. At time T1, the comparator output (COMP_OUT) transitions from low to high causing the first flip-flop ( 710 ) to set the Q output ( 714 ) to a logic high signal. A short time after the equalizer output signal drops below the top peak level (at time T2), the timing signal T2_SIG pulses from high to low, causing the second flip-flop ( 720 ) to latch the first sampled data point ( 714 ) to the Q output ( 724 ). At time T3 the equalizer output signal further drops from a high level to a low level and the T3_SIG timing signal pulses from low to high for a fixed time interval. The T3_SIG_pulse causes the first flip-flop ( 710 ) to reset the output ( 714 ) to a low logic level, and the Q output ( 724 ) of the second flip-flop ( 720 ) is latched into the Q output (T1_SP 1 ) of the third flip-flop ( 730 ). At the same time, the T3_SIG pulse causes the fourth flip-flop to latch the comparator output (which is low) into the Q output (T3_SP 1 ) of the fourth flip-flop ( 740 ). A short time after the equalizer output transitions from a high level to a low level, the T2_SIG timing signal will pulse low again, causing the second flip flop ( 720 ) to set the Q output ( 724 ) to a low logic level, and simultaneously resetting the comparator output to a low logic level. 
   In  FIG. 9 , point P 1  shows that Equalizer Output signal is above the top peak level and point P 2  shows that Equalizer Output signal is below the top peak level. By using the sampling circuit previously described, T1_SP 1  corresponds to a logic high level at time T3 and T3_SP 1  corresponds to a logic low level at time T3 respectively. Thus, sample points T1_SP 1  and T3_SP 1  match with the fact that Equalizer Output signal is above top peak level at time T1 and below top peak level at time T3. In other words, the sampling circuit functions as a means of translating the condition of the equalized data signal to a logic high or low as reflected by sampling points T1_SP 1  and T3_SP 1 . Sampling points T1_SP 1  and T3_SP 1  may be used to determine if a particular persistent condition occurs. 
   Each time the incoming data (COMP_OUT) transitions from low to high, the Q output ( 714 ) of the first flip-flop ( 710 ) will change to a high logic level. The sampling window is maximized by sampling the comparator output signal instead of using another timings signal to latch the comparator output. The sampling window is defined as the time interval between the positive edge of the data signal at time T1 and the rising edge of the T3_SIG timing signal. Since the circuit utilizes pulse signals T2_SIG and T3_SIG that are generated from the incoming signal, the equalizer system uses less power without the need for a high frequency clock generator. The flip-flops used in the sampling circuit consume very little power, have low set-up and hold times, and need not be high speed. Standard cell flip-flops and logic can be used allowing the equalizer design to be scalable. 
   The sampling points (T1_SP 1 , T3_SP 1 ) from a sampling circuit such as shown in  FIG. 7  are used to algorithmically determine adjustments to equalizer gain and amplitude settings in the equalizer system. By collecting the sample data (T1_SP 1 , T3_SP 1 ), the equalizer control logic makes decisions on equalization control based on an averaging algorithm. Similarly, the amplitude control logic makes decisions on amplitude control based on another averaging algorithm. 
   The above specification, examples and data provide a complete description of the manufacture and use of the composition of the invention. Since many embodiment of the invention can be made without departing from the spirit and scope of the invention, the invention resides in the claims hereinafter appended.