Abstract:
Circuitry and method for synchronizing operating speeds of signal processing devices to the data rate of a signal. It applies in particular to Compact Disk (CD) and Digital Versatile Disk (DVD) drives to be used with portable devices. The circuitry does not require clock synchronization speeds in excess of the instantaneous data rate used by the disk drive and also reduces power consumption.

Description:
FIELD OF THE INVENTION 
     The present invention relates to circuitry having a wide capture range (bandwidth), particularly suitable for use with high-speed drives. Specific examples include drives using either Constant Linear Velocity (CLV) modulation or Constant Angular Velocity (CAV) modulation, or both. 
     BACKGROUND 
     There is a need for the normal playback speed of disk drives, in particular, Compact Disk (CD) or Digital Versatile Disk (DVD) drives, to be readily upgraded for use with faster disk drives. There are two types of modulation used to read to or write data from a disk: Constant Linear Velocity (CLV) modulation and Constant Angular Velocity (CAV) modulation. 
     CLV provides a way of reading and writing data to disk that uses a single track in a continuous spiral from the center of the disk to the circumference, instead of several concentric circles as with CAV modulation. Each sector of a CLV disk is the same physical size and the disk drive continuously varies the rate at which the disk spins so that as the read/write head moves from the center of the disk, the disk slows down. In other words, the disk rotation speed necessarily varies with the radius of the disk so that the read data rate can be held constant. The faster that the disk is able to spin, the shorter the access times needed since the rate of change is a rate dependent on a faster overall rotating speed. Since the CLV disks have retained the same diameter for the sake of uniformity, increasing the overall speed of rotation means that the data on the data-efficient CLV modulated disks will need to be accessed in correspondingly shorter times and the read rate adjusted to be correspondingly faster. CLV also provides for more data storage on the disk than drives using CAV modulation. 
     CAV causes the disk to rotate at a constant speed, with the number of bits in each concentric track being the same. Because the inner tracks are smaller in diameter than the outer tracks, the density on the outer tracks is less than optimum. Thus the problem of data access is not as critical with the less data-efficient CAV disks as compared to CLV. The CAV disk does permit fast data retrieval and is well suited to storing high-resolution photos or video. The CAV disk can be designed to operate with an access time suited to the most critical inner track where data density is the greatest with no concern for holding the read rate constant as with the variable rotation speeds of CLV disks. However, as drive rotation speeds increase, even the access times for reading data on the inner tracks of the CAV disks will become a critical design parameter. For example, when the track jump commands enable the actuator to move from inner tracks to outer tracks, the actuator moves faster than the disk rotation speed and the read rate changes as a function of radius thus engendering a requirement for faster access and seek times to accommodate this change. 
     The codes used to program the disk drives (either CD or DVD) are “DC-Free” codes, i.e.; the long-term average duty cycle is 50%. CDs use an eight-to-fourteen bit code termed EFM while DVDs use an eight-to-sixteen bit code termed EFM Plus. The EFM system maps eight user bits into fourteen channel bits, while using only a subset of all possible 14-bit words. The EFM Plus system maps eight user bits into 16 channel bits while using a subset of all possible 16-bit words. 
     For CD drives, only the words that satisfy the run length constraints of no fewer than three channel bits and no more than 11 channel bits between transitions are used. The code is called the (2,10) Run Length Limited code. This yields a minimum of two zeroes between the marks and a maximum of ten zeroes between the marks. As an example, 100100 is written as 3T/3T and yields the maximum frequency while 1000000000010000000000 is written as 11T/11T and yields the minimum frequency. The encoder appends three additional channel bits (to the maximum of 11) for charge control. This forces the duty cycle to 50%. The short sector in the CD Read-Only-Memory (ROM) drive consists of 588 channel code bits and has only one synchronization pattern: 11T/11T. There is one synchronization pattern in every sector (588T) and it is not treated as normal data. The data rate of incoming data can be determined by calculating the duration of this incoming 11T/11T-synchronization pattern. The 11T pattern is the longest signal pattern for a CD drive but there can be no 11T/11T combination in the data stream for a conventional CD-ROM&#39;s drive. 
     For DVD drives, only words that satisfy the run length constraints of no fewer that 3 channel bits, and no more than 11 channel bits, between transitions are used, i.e., the same (2,10) Run Length Limited code as for the CD drives. However, there are four states of the conversion table and each state is selected by a DC component suppress control (DCSC) algorithm, permitting the suppression of the DC component of each. The short sector in the DVD-ROM drive consists of 1488 channel code bits with only one synchronization pattern: 14T/4T. There is one synchronization pattern in every sector (1488T) and it is not treated as normal data. The data rate of incoming data can be determined by calculating the duration of this incoming 14T-synchronization pattern. The 14T pattern is the longest signal pattern for a DVD&#39;s drive but there can be no 14T/4T combination in the data stream (the EFM Plus Modulation rule identifies it as violated code) for a DVD-ROM&#39;s drive. The present invention provides a solution by significantly increasing the PLL&#39;s (or PLL equivalent&#39;s) capture range. 
     DVD-ROM drives use a Non-Return-to-Zero (NRZ) format. In EFM Plus code, the signals are inverted at the center of each “1” in the data stream. 
     Conventional systems use the following process to increase the capture range of the PLL (thus reducing seek/access time): 
     a. The synchronization pattern is detected as the T max  pattern and the clock&#39;s counter is set to count at least twice the rate of the channel code at the maximum disk speed associated with the VCO synchronization clock of the PLL. 
     b. Upon detection of the T max  pattern, the counter data is transferred to a microprocessor and the data read/write speed is calculated. 
     c. The calculated speed is reloaded to the VCO synchronization clock and the T max  pattern is compared to the read/write data rate. 
     d. If the VCO&#39;s frequency is not synchronized with the read/write data rate, a “kick pulse” is generated by the microprocessor to adjust the frequency of the VCO. 
     Conventional technology has required the T max  pattern detection to occur at a clock rate of two to four times the read/write data rate. Assuming the clock&#39;s counter has a 2X-pattern detection rate, the count value variation would be 28±2 (maximum) for the 14T DVD&#39;s drive. Further, the VCO synchronization clock would be programmed to ½ the clock counter&#39;s frequency. The capture range when in the phase detection mode of the PLL requires ±7% variation about the VCO&#39;s center frequency to accommodate variations in frequency due to the process itself, power supply voltage fluctuations, and temperature, among others. Because this assures the need for a kick pulse (the VCO&#39;s center frequency is continuously being adjusted) more power is dissipated because of the microprocessor&#39;s contribution to the adjustment and the need for continuous adjustment. When the conventional system is called on to perform this adjustment over very short time intervals, such as those associated with the new higher disk rotation speeds, it encounters physical limits to processing times. Therefore, there is a need for overcoming this limitation with a basic design change. 
     SUMMARY 
     The preferred embodiment of the present invention&#39;s wide capture PLL (or PLL equivalent) has two modes: frequency detection mode and phase detection mode. The frequency detection mode consists of three steps: 
     a. T max  Detection. The Time Base Generator (TBG) VCO&#39;s clock is used to find the longest mark and the TBGVCO&#39;s clock frequency is used for any frequencies higher than the target read/write data rate. The longest mark is the synchronization mark. In DVD drives, the 14T pattern is used as the synchronization mark. This 14T pattern is the “violated code” of EFM Plus that occurs every 1488 bits in the short frame length. The T max  window is opened approximately six to ten times during the short frame length. The maximum count value encountered during this period is stored in the T max  register. 
     b. In the synchronization detection step, the data synchronizer voltage controlled oscillator (DSVCO) and the TBGVCO&#39;s frequency are the same, with the TBGVCO locked to the DSVCO. During the synchronization step, the DSVCO&#39;s frequency is changed to the proportional frequency, i.e., 14/T max . Unlike conventional systems using PLLs, the proportional frequency is generated by a current divided from the TBGVCO to the DSVCO&#39;s center frequency. 
     c. In the fine adjustment step, once the center frequency of the DSVCO is set, the reference clock is set to the data synchronizer&#39;s output in order to detect the appropriate synchronization pattern (14T/4T for DVD or 11T/11T for CD). Using the detection window and an up/down counter sets the DSVCO&#39;s frequency. The detection window identifies the next estimated synchronization pattern period (e.g., 1488T in a DVD-ROM&#39;s driver) and the up/down counter is used to fine adjust the DSVCO&#39;s frequency. 
     When the synchronization pattern is detected in the detection window, the PLL moves to a conventional phase detection mode. 
     Some of the salient advantages of the present invention are that it provides: 
     lower data rates by using a current divider to the DSVCO. 
     clock speeds no higher than the data read/write rate for the disk drive. 
     a near capture-free Phase-Locked Loop (PLL) for a high-speed drive, in particular either CD or DVD drives. 
     very fast seek time for reading from or writing to a data storage component. 
     a very fast access time for reading from or writing to a data storage component. 
     a more efficient method requiring less energy to implement. 
     a time base generator (TBG) during wide capture operation. 
     a synchronization detection “power down” mode to the entire circuit. 
     an automatic power down enabled through a register control bit. 
     detect output monitor pins synchronized through register control bits window detection accuracy synchronized through a register control bit. 
     a T max  counter read-only register for capturing the highest count. 
     an up/down counter read-only register for capturing the count used in current scaling. 
     a detect signal input to reset the data rate detection. 
     two methods of current scaling, one for a wide capture range step and one for a fine adjustment step. 
     application to any system using a PLL circuit. a capability of working without using a time base generator (TBG) PLL. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 depicts the synchronization pattern detection operation. 
     FIG. 2 provides a Sync7 interface description. 
     FIG. 3 is the input/output (IO) list for the Sync7. 
     FIG. 4 is a block diagram of Sync7. 
     FIG. 5 is a description of wide capture frequency detection step A (T max ). 
     FIG. 6 is a description of wide capture frequency detection step B. 
     FIG. 7 is a description of the fine adjustment step. 
     FIG. 8 is a synchronization pattern detection-timing chart for a DVD. 
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     A salient feature of the current invention is the provision of synchronization to high speed devices without requiring the synchronization clock to operate at speeds higher than the device&#39;s own input operating speed. The preferred embodiment of the present invention provides a system and method for matching the data synchronization clock speed to that of representative higher state-of-the-art disk drive speeds, in particular CD or DVD drives. 
     A simplified block diagram description of the synchronization detection circuit (for a DVD) of the present invention is shown in FIG.  1 . There are two T max  counters  1  and  2 , two Tmax registers  3  and  4 , a T max  value comparator  5 , a synchronization pattern detection circuit  6 , a current divider circuit  7 , an up/down counter  8 , a data synchronization VCO  9 , a TBG VCO  10 , a multiplexer  11 , an inverter  12 , two gates  13  and  14 , and a 16-bit counter  15 . Certain of these components, for example, the registers, serve functions at different stages of operation and thus can be considered to be common components of separate circuits. This saves the designer both in space on the chip and in power consumption. 
     The frequency synthesizer PLL (used as a time base generator (TBG) in this example) generates a fixed frequency for counting the synchronization pattern. The counter counts the number of TBG clock periods of the data in either high or low (inverted) state, stores the highest count and automatically adjusts the VCO&#39;s frequency to the rate of the incoming data stream by scaling down the current to the DSVCO. The DSVCO frequency is calculated from the relationship: 
     
       
           F =( x/N ) F ( TBGVCO )  (1)  
       
     
     Where: 
     x=11 for CD drives 
     x=14 for DVD drives 
     N =the maximum count stored in the T max  register. 
     The first step of the frequency detection mode is termed T max  detection step (step A). 
     In the wide capture step (step B) of the frequency detection mode, the incoming data (Rd 1 a and Rd 1 b in FIG. 3) are ANDed together with the TBGVCO&#39;s frequency (e.g., 80 MHz) and fed to CTA  1 , the first Current Mode Logic (CML) 6-bit counter clock input, Clk. CTA  1  counts the number of clock periods in the Clk input. CTB  2 , a second CML 6-bit counter performs the same function as CTA  1 , except that it inverts the incoming data. This results in CTA  1  counting the incoming data held at a high state and CTB  2  counting the data held at a low state. Whenever the incoming signal level changes (high to low or vice versa), the data from the counter that counted the immediately preceding level is transferred to the first register TRD  17  where it is stored before the counter is reset. TRD  17  and the second register TRA  18  are initially set to zero. The data in TRD  17  are compared to that in TRA  18 . If the value in TRD  17  is smaller than the value in TRA  18 , then the comparator COMP 6   20  outputs nothing. However, if the value in TRA  17  is larger than that in TRA  18  then COMP 6   20  outputs a “load” signal that loads the value from TRD  17  into TRA  18 . The process is iterated and TRA  18  stores the highest value of input data, Rd 1 a and Rd 1 b, held in a particular level. 
     The fine adjustment step is defined by the switching of the clock frequency from the TBGVCO frequency to the DSVCO frequency (F). Synchronization pattern is checked for position within the window for every sector of data (1488T for DVD and 588T for CD). Accuracy is nominally held to either ±3% or ±10% of Phase Detector Enable Signal (Phden=1). If the synchronization pattern is started before the window period time frame (e.g., &lt;1472T for a 1% accuracy window setting for a DVD drive), the DSVCO&#39;s frequency is stepped up by increasing the current to the VCO. Conversely, if the synchronization pattern is started after passing the window (e.g., &gt;1504T for a 1% accuracy window setting for a DVD drive) the frequency of the DSVCO will be stepped down by decreasing the current to the VCO. The process is iterated until the synchronization pattern appears within the window period. Once in the window, the frequency is locked and further attempts at changing the frequency are ignored. 
     This largest value stored in register TRA  18  is now the synchronization pattern count since it has the longest duration (i.e., 11T for CD and 14T for DVD). When the TBGVCO&#39;s  10  count reaches 40960 for DVD (24576 for CD), the data stored in TRA  18  are loaded into register TRB  4 . This 6-bit data are then read from the serial port register, T max  R 1 . The approximate DSVCO&#39;s  9  PLL center frequency is calculated using the T max  R 1  value. For example, if the T max  R 1  value is 40 counts, then the data rate of incoming data is 80/(40/14)=28 Mbs. Thus the value for the current, DAC (DSVCO  9  current)  7   a  in FIG. 1, will be reduced to match that of the DSVCO  9  so that the DSVCO&#39;s  9  frequency is approximately 28 Mhz. 
     In the fine adjustment step, when the current of the DSVCO  9  PLL is adjusted to yield the appropriate center frequency, the reference clock is changed to that of the DS PLL output (DSVCO) and the detection of the synchronization pattern is now done using this clock. The clock rate approximates the actual incoming data rate. Thus CTA  1  and CTB  2  count the synchronization pattern (11T for CD and 14T for DVD). 
     The outputs of CTA  1  and CTB  2  are fed to synchronization pattern detector ZRDT  21  in FIG. 4 to determine when the synchronization pattern has been established. For a DVD driver, ZRDT  21  searches for 13 clock cycles and outputs a synchronization signal when the pattern has been established. (For the CD driver, the ZRDT  21  searches for 11 clock cycles at one level and 11 at the other level.) Both counters, CTA  1  and CTB  2 , are continuously updated and adjusted as input data change. 
     Detection of the synchronization pattern generates a reset signal at synchronization detector SYCDT  6  in FIG.  4 . This initializes the  16 -bit counter in counter CTR15  23  in FIG. 4 to zero. CTR15  23  is synchronized to the DSVCO  9  clock&#39;s frequency. Window detector Winddec10  24  in FIG. 4 traces the number of DSVCO  9  clock periods in CTR15  23  and generates a signal level called “window”  24   a  in FIG. 4 when the count is within the window accuracy set by Windw[1:0] bits  24   b  in FIG.  4 . Windw[1:0] bits  24   b  consist of two bits used to select the desired accuracy (i.e., 1, 2, 3, and 10%) for the window to detect the synchronization pattern. Windw[1:0] bits  24   b  are controlled by a SYCR[2:1] bit (not shown). This signal  24   b , as well as a synchronization signal from ZRDT  21 , (not shown) is fed to SYCDT  6  for evaluation. 
     SYCDT  6  determines when the synchronization pattern occurs, i.e., before or after the window. If the pattern occurs before the window, the DSVCO  9  clock&#39;s frequency is too low, and a signal is sent to increase it by altering the current  7   a . Conversely, if the pattern occurs after the window, the frequency is too high, and a signal is sent to decrease it by altering the current  7   a . Whenever the synchronization pattern occurs outside the window, the SYCDT  6  generates an up/down count signal  6   a  in FIG.  4 . This signal together with a clock signal is forwarded to up/down counter UDCT  8  in FIG. 4 indicating the need to perform a shift in frequency. Otherwise, if the signal is within the window, a signal designated Phden  37  in FIG. 7 is generated. This is a phase detector enable signal UDCT [4:0]  8   a  in FIG. 4 that indicates the fine adjustment step is complete. If the signal does not fall within the window, the process is iterated until it does. 
     UDCT  8  accepts the up/down count signal  6   a  and programs an internal 5-bit register (not shown) accordingly, via the enable signal  8   a . The register is initially held at a center position of 5′b10000. If an up count is required, the register is incremented by 1, and if a down count is needed, decremented by 1. The range of adjustment for the fine adjustment step is approximately 5′b00000 (−16%) to 5′b11111 (+15%) with a step size of about 1%. If either “00” (i.e., all zeroes) or “1Fh” (i.e., all ones) is detected in UDCT  8 , an overflow signal, designated udctrover 2  Table in FIG. 3, is set to indicate an overflow condition. The current sources CSA  25  and CSB  26  accept the 5-bit data  8   a  from UDCT  8  and generate an electrical current, IOUt  25   a  and  26   a  in FIG. 4, based on the value of the 5-bit data  8   a . 
     Frequency Detection Step A. 
     CTA  1  and CTB  2  are  6 -bit counters that count “up” whenever there is a rising edge at their respective clock input, Clk la and  2   a  in FIG.  4 . Setting the counter back to zero is done by three “reset sources”: Rst 1, 2, and 3  1   b, c, d  and  2   b, c, d  in FIG.  5 . Assuming both CTA  1  and CTB  2  are initialized and set to zero, when one of the respective input data signals Rd 1 a  1   e  and Rd 1 b  2   e  is held at one level, one of the clocks Clk  1   a  and  2   a  follows the TBGVCO&#39;s  10  clock while the other is disabled as the input data is inverted. For example, if Rd 1 a  1   e  is held at a high level, the CTA clock  1   a  is synchronized to the TBGVCO&#39;s  10  clock and the CTB clock  2   a  is disabled as input data Rd 1 a  1   e  is inverted. CTA  1  then starts to count the number of TBGVCO  10  clock periods. When Rd 1 a  1   e  is changed to a low level, then CTA  1  stops counting (without being reset) and CTB  2  starts counting. 
     The detection of the synchronization pattern is done by ZRDT  21 . The purpose of ZRDT  21  is to detect the synchronization pattern and to generate a reset signal  21   a  and  21   b  in FIG. 4 to reset the counter. For example, as the CTB  2  count reaches 2X, ZRDT  21  initiates a signal designated LDO  21   c  in FIG.  5 . The LDO signal  21   c  is then passed through external logic  27  in FIG.  5  and two signals are generated. A “Load” signal  27   a  in FIG. 5 is generated to load the value in CTA  1  into TRD  17 . The second signal LDO  21   c  is generated to reset CTA  1  to zero. CTB  2  is not reset since the Rst 1 signal  2   b  is held at the low level. At the same time MUX  28  in FIG. 4 is switched from A to B input as CTB  2  continues to count. 
     The process is iterated when input data Rd 1 a  1   e  changes level. TRD  17  continuously updates the count. TRD  17  compares incoming data with previously stored data to determine the highest count reached at any given level. 
     Frequency Detection Step B—Comparison. 
     The stored value from TRD  17  is compared with the value in TRA  18 . To do this, TRA  18  is set to zero initially and comparison is done in comparator COMP6  20 . COMP6  20  generates an output pulse whenever the A [5:0] input  1   f  in FIG. 5 is greater than the B[5:0] input  2   f  in FIG.  5 . This pulse loads the data from TRD  17  to TRA  18 . This is the highest count that the TBGVCO&#39;s  10  clock captured. It is viewed at the serial port register, T max  R 1 . 
     T max  R 1  values are delivered to TDA  29  in FIG.  4  and TDB  30  in FIG. 4 in order to set the appropriate current to be fed to DSVCO  9 . TDA  29  and TDB  30  generate current based on the value of T max  R 1 . In the T max  R 1  detection phase, the reference current, DSVCOI  31  in FIG. 6, is sent to TDB  30 . TDB  30  outputs the same reference current, adding it to the current from current source CSB  26 . At this time CSB  26  does not generate any current. The summed current, designated IDSVCO  32 , is forwarded to DSVCO  9 . At this time there is no change in the reference current, thus DSVCO  9  is running at its reference frequency. 
     When the count, now referencing the frequency from TBGVCO  10 , reaches 40960 for DVD (24576 for CD), the DSVCOI  31  current is scaled as a function of the T max  R 1  value. TRB  4  acts as a “current mirror” thus enabling the effective resistance at the emitter to be controlled by the Tmax RI count. The effective resistance (not shown) and the DSDIV [1:0] input current  33  in FIG. 6 control the amount of “scaled current” to be sent to CSB  26 . The frequency divider is now selected. 
     If the DSVCO frequency is not to be divided (as determined at SYCR [7:5]), the reference current adds to the current output, i.e., DSVCOI  31 , of CSB  26 . For example, if the T max  R 1  count is 14 and the ratio of the resistance in the current mirror(s) is 0.85, this current is proportional to 12T (i.e., 0.85·14T) of the total of 14T (for DVD). TDB  30  also initiates a 3T current to CSB  26  to fine adjust the frequency of DSVCO  9 . 
     When the detection steps are completed, the clock frequency is changed from that of TBGVCO  10  to that of DSVCO  9 . CTR15  23  counts the incoming clock periods. At the Winddec10  24  the accuracy of the window period is set by two bits, wind: [1:0]. For example, if wind: [1:0] is set to “00,” then the window signal is shifted to the high level when the clock period count is within ±1% of a sector. (For DVD, a sector is 1488T and for CD, a sector is 588T.) Any value other than this means that the window signal stays at the low level. 
     The signal is then sent to SYCDT  6 , combined with the synchronization signal from ZRDT  21 , and the amount of error in DSVCO&#39;s  9  frequency is calculated. If the synchronization signal is set before the arrival of the window, SYCDT  6  issues an up signal together with a pulse designated udclk  6   b  in FIG. 7 to UDCT  8  in order to increment the counter. The 5-bit counter  8 , in turn, controls the amount of current mirror output in CSA  25  and CSB  26 . The counter  8  counts down when the synchronization signal occurs after the window arrives. 
     Initially, TDB  30  does not supply any current to CSB  26 , and UDCT  8  is held at the intended center frequency, 5b′10000. In the fine adjustment step, the current at TDB  30  is scaled down to 12T and ¼ of the 12T current, i.e., a 3T current, is sent to CSB  26 . CSB  26  then outputs a current that is ⅔ of the incoming 3T current. UDCT  8  adjusts the 3T current from 5′b00000 to 5′b11111, therefore the resolution becomes &lt;1% [({fraction (1/32)}×4)/14×100]. This yields a maximum adjustment range from approximately −16% to +15% of input data frequency. 
     Windec10  24  generates an output signal when the count reaches 40960 for DVD (24576 for CD) when referenced to the TBGVCO&#39;s  10  clock. This signal is then passed through external logic  27  to load TRA  18  into TRB  4 . This LD signal  34  in FIG. 6 switches the TBGVCO&#39;s  10  clock frequency to the DSVCO&#39;s  9  clock frequency. The LD signal  34  also generates a signal DL50  35  in FIG. 7 to SYCDT  6  to indicate when it has exceeded 50% of one frame of data (one frame of DVD is 1488T and one frame of CD is 588T). 
     If the synchronization signal  36  in FIG. 7 is detected during the window period, the Phden signal  37  is set. This marks the completion of the second part of frequency detection mode. The data synchronizer then enters the “zero phase” restart mode. SYCDT  6  will set signal Outof5  38  in FIG.  7  and the synchronization process will be stopped if either five DL50  35  signals are encountered or a synchronization pattern was missed. 
     Finally, if the powerdb bit (not shown) is set, the entire Sync7 circuit FIG. 4 will be powered off. The option to set “auto power bit” provides the capability of shutting power down to the entire Sync7 after the fine adjustment step has been completed. 
     EXAMPLE 
     Undivided. 
     After 24576 counts (CD) or 40960 counts (DVD), the following determination is performed: 
     
       
         
               
               
               
               
             
               
               
               
             
           
               
                   
               
             
             
               
                 Assume: 
                 T max   
                 = 
                 50 
               
               
                   
                 DIDIV 
                 = 
                 0 
               
               
                   
                 DSVCOI 
                 = 
                 100 μA (IREF) 
               
               
                   
                 TBGVCO 10 frequency 
                 = 
                 80 MHz 
               
               
                 Then: 
                 Frequency required for the VCO: 
               
               
                   
                 14/50 × 80 MHz 
                 = 
                 
                   22.4 MHz 
                 
               
             
          
           
               
                 Current needed to scale down should be: 
                   
                   
               
               
                 IDSVCO = 14/50 × 100 μA 
                 = 
                 
                     28 μA 
                 
               
               
                 Adding two current components to IDSVCO: 
               
               
                 Current from the resistance ratio at TRB 4: 
               
               
                 12 T current = 
               
               
                 (1.12k//2.42k//17.938k)/2.99k × 100 μA 
                 = 
                 
                   23.98 μA 
                 
               
               
                 3 T current to CSB 26: 
               
               
                 3/12 × 23.98 μA 
                 = 
                 
                    6.0 μA 
                 
               
               
                 If the up/down counter (UDCT 8) is centered in window: 
               
               
                 Current mirror ratio at CSB 26: 
               
               
                 2/3 × 3 T current = 2/3 × 6.0 μA 
                 = 
                 
                    4.0 μA 
                 
               
               
                 Total current at IDSVCO = (3) + (1): 
               
               
                 4.0 μA + 23.98 μA 
                 = 
                 
                   27.98 μA 
                 
               
               
                   
               
             
          
         
       
     
     With 27.98 μA applied to the VCO, the frequency output will approximate the required 22.4 MHz. 
     For the case when DIDIV is divided, i.e., DIDIV=1, then the frequency of the VCO is required to be doubled. Doubling the total current accomplishes this in a straightforward fashion. 
     FIG. 8 provides a time line showing the two steps of the frequency detection mode after T max  has been set and the single conventional step of phase detection. Line  1  represents the SYNCEN input to enable the process. Line  2  represents the setting of the 16-bit counter using the TBGVCO&#39;s clock  10  to count the first step of frequency detection and the DSVCO&#39;s clock  9  to count the second or fine adjustment step. TBGVCO is represented by Line  3  and the 6-bit counters CTA  1  and CTB  2  determine the Tmax value. Line  4  represents the DSVCO&#39;s  9  clock, allowed to free-run at the TBGVCO&#39;s  10  clock rate during the initial detection period and reset to the adjusted center frequency determined by 14/T max ·TBGVCO frequency. Line  5 , RDO, represents the raw data input. Line  6  provides the synchronization pattern detection using the 6-bit counter. It changes the DSVCO  9  clock center frequency by the value in UDCT  8  if the synchronization signal is not in the window. Line  7  represents the synchronization window detection and setting based on a ±3% accuracy. Line  8  represents the start of the Phden signal  37  initiating the transition to the conventional phase detection mode. Line  9  represents the pulse train that will change the frequency from that of the TBGVCO to that of the DSVCO. It is calculated as TBGVCO frequency/4·DSVCO divider bit. Line  10  represents the synchronized data. 
     The foregoing describes the salient features of the present invention for achieving wide capture range, and should not be interpreted as limiting the application of, method of operation, or uses for the present invention to that specified in the foregoing. While the wide capture range apparatus and method has been shown with specific components and subsystems, and further described with regard to a specific order of implementation, it will be understood by those skilled in the art that various other changes in the selection of components and use with a different order of steps, or other details, may be changed without departing from the spirit and scope of the present invention.