## 2 System Model
\(\mathcal{G}_{W}^{o}\) is the highest antenna gain for the beam's main lobe, \(\mathcal{G}_{W}^{E}\) is the single antenna element gain in the \(\theta\) and \(\phi\) directions, and \(\mathcal{G}_{W}^{A}\) is the antenna array gain using uniform radiation. The antenna's square array gain is defined as: [30]  
\[\mathcal{G}_{W}^{A}=\left(\dfrac{\sin\biggl{(}\dfrac{N_{W}(\Xi_{x}+\bigwedge_{ x})}{2}\biggr{)}}{N_{W}\sin\biggl{(}\dfrac{(\Xi_{x}+\bigwedge_{x})}{2}\biggr{)}} \dfrac{\sin\biggl{(}\dfrac{N_{W}\bigl{(}\Xi_{y}+\bigwedge_{y}\bigr{)}}{2} \biggr{)}}{N_{W}\sin\left(\dfrac{\Bigl{(}\Xi_{y}+\bigwedge_{y}\Bigr{)}}{2} \right)}\right)^{2}, \tag{2}\]  
where \(\Xi_{x}=\
u_{x}\Psi_{x}\delta_{x}\) and \(\Xi_{y}=\
u_{y}\Psi_{y}\Delta_{y}\) such that \(\Delta_{y}=\sin(\theta)\sin(\phi)\) while \(\delta_{x}=\sin(\theta)\cos(\phi)\). Furthermore, the wave number is defined as \(\
u_{x}=\
u_{y}=2\pi f_{c}\), where \(f_{c}\) indicates the frequency. The plate thickness is specified by \(\Psi_{x}=\Psi_{y}=c/2f_{c}\), and the progressive phase shift is \(\bigwedge_{x}=\bigwedge_{y}=0^{\circ}\). The antenna element gain is defined as [31]  
\[\mathcal{G}_{W}^{E}=G^{E,\max}-\min\{-\Bigl{(}G^{*}(\theta^{E})+G^{**}(\theta _{x})\Bigr{)},\ominus\}, \tag{3}\]  
\[\text{where}\ \ \ G^{*}\ \ =\ \ -\min\Biggl{\{}-12\biggl{(}\dfrac{ \theta^{E}-90^{\circ}}{\mathcal{V}}\biggr{)}^{2},\ominus\Biggr{\}},\ \ G^{**}\ \ =\ \ -\min\Biggl{\{}-12\biggl{(}\dfrac{\theta^{E}}{\mathcal{H}}\biggr{)}^{2}\ominus \Biggr{\}}\ \ \text{and}\]  
\[\theta^{E}\!\!=\!\!\tan^{-1}\!\left(\dfrac{1+\sin^{2}(\theta_{x})}{\sin(\theta _{y})}\right)^{0.5}\Biggr{\}}.\ G^{E,\max}\text{ is typically considered to be 8 dBi. The reflected x-axis and y-axis beam width is given by \(\mathcal{H}=\mathcal{V}=65^{\circ}\). \(\ominus=30\) dB represents the limit of antenna side lobes, whereas \(\ominus=30\) dB represents the front-to-back antenna ratio.  
To ensure equal radiated power from \(N\) antennas, the greatest gain coefficient with \(\theta=0^{\circ}\) using Equation (2.22) of [30] is  
\[\mathcal{G}_{W}^{o}=\frac{4\pi}{\int_{0}^{2\pi}\int_{0}^{\pi}G_{W}^{A}\sin( \theta)d\theta d\phi}. \tag{4}\]  
An exclusive path loss approach to millimeter waveband-based connectivity has not yet been defined for remote regions; therefore, 3 GPP's path loss model for remote regions is taken into consideration. We assume a millimeter waveband-dependent path loss framework for rural terrain (as presented in [23; 32]) and configure the network configurations of rural environments provided by rural macros (RMas), rather than dense urban areas. To analyze the dense urban areas like urban macro (UMa) or urban micro (UMi), the path loss models presented in [31] for UMa or UMi can be considered. Since UMa and UMi pathloss models are conventionally considered when the base station height limitations are up to 25 m and 10 m, respectively, whereas RMa base station heights are up to 150 m, taking RMa into account allows us greater freedom in selecting the base station altitudes of the considered C-V2X network assisted by UAVs. The path loss is expressed for building altitudes, \(H_{b}\), up to 50 m and wireless tower altitudes up to 150 m and is given as follows [31]:  
\[\mathcal{Z}(z) =20\log_{10}\biggl{(}\frac{40\pi zf_{c}}{3}\biggr{)}+\min\Bigl{\{} 0.03H_{b}^{1.73},10\Bigr{\}}\times\log_{10}(z)-\min\Bigl{\{}0.044H_{b}^{1.73}, 14.77\Bigr{\}}\] \[+0.002z\log_{10}(H_{b}). \tag{5}\]  
The jamming devices are distributed using an MCP such that the parent nodes or the cluster centers are distributed in a 2D space using PPP. The child nodes, or the jamming devices, are placed around the cluster center in a circle of radius, \(\mathbf{r}_{J}\), using a uniform distribution. The jamming devices are distributed uniformly within a cluster of a circular radius. This is because, for the clustered jamming, the system modeling of jammers considers that the jammers are distributed according to an MCP.