esa-sceva/satcom-chunk-collection huggingface dataset:
## 3 Extraction of Intermittent Failure Feature
### Generalized Severity of Intermittent Failure  
According to the four wire method, the measured voltage is \(U_{\mathrm{H}}\) (intermittent failure upper boundary, \(U_{\mathrm{H}}=U_{\mathrm{S}}\)) when the connector is completely disconnected (permanent fault) and the  
Figure 8: Overall scheme of residual life prediction for electrical connectors.  
Figure 9: Test principle of contact resistance of four line method.  
measured voltage is less than \(U_{\rm L}\) (intermittent fault lower boundary, \(U_{\rm L}=R_{\rm th}U_{\rm S}/(R_{\rm th}+R_{\rm S})\)) when the connector is in good contact. In the measurement interval of (0, \(t\)), the intermittent failure curve of electrical connector \(U_{\rm IF}\)(t) can be obtained as shown in Figure 10.  
For convenience, we defined severity of intermittent failure, which is given by  
\[I=\int_{t}^{t+\Delta t}\left[U_{R}(t)-U_{L}\right]dt \tag{18}\]  
where \(\Delta t\) denotes the test window, and \(I\) denotes the severity of intermittent failure.  
In fact, \(I\) is the area of the shadow part enclosed by the contact voltage curve and the Intermittent failure lower boundary \(U_{\rm L}\). Further, data is processed for the normalization of intermittent fault severity \(I\).  
\[\widetilde{I}=\frac{1}{\Delta t}\cdot\frac{\int_{t}^{t+\Delta t}\left[U_{R}(t )-U_{L}\right]dt}{U_{H}-U_{L}} \tag{19}\]  
where \(\widetilde{I}\) is defined as the generalized severity of intermittent failure, and \(\widetilde{I}\in(0,1)\). It means contact in normal state if \(\widetilde{I}=0\), it means the permanent fault if \(\widetilde{I}=1\), otherwise the connector suffered intermittent failure.  
According to MIL-PRF 32516 \"electronic Test Equipment, Intermittent Fault Detection & Isolation\", the intermittent failure duration should not exceed 5 ms, otherwise a permanent fault is considered. Therefore, the length of the test window is set to 5 ms, thus, \(\Delta t=5\) ms. Further, the sequences of generalized intermittent failure severity can be obtained through slipping the test window with a certain step length. Let the step length of slipping be \(T\). it worth mentioned that the step length \(T\) should be less than \(\triangle t\) to prevent the information leakage of intermittent failures.
## 6 Development Trends and Prospects  
The current popular research directions include data-driven intelligent detection, multi-sensor fusion methods, real-time online monitoring, etc., indicating that the research on bearing fault detection methods is developing in a more intelligent, integrated, and real-time direction. In order to improve practicality, it is also important to study early fault prediction, enhance the interpretability of deep learning models, and reduce costs, as shown in Figure 11.
## 5 Conclusions  
The following conclusions can be drawn from the conducted research:  
1. The proposed method of hyperspectral imaging allows for a quantitative assessment of the spectral parameters of dyes implanted in pig skin and, thus, optimization of the laser parameters necessary for its removal.
2. The laser application causes a decrease in reflectance for all tested dyes except for white. White pigment is the most difficult to remove due to its high reflectivity.
3. For all dyes, except for white, a decrease in GLCM contrast and an increase in homogeneity were recorded, which indicates that after laser treatment, dyes are distributed more homogeneously in the skin.
4. The increase in the homogeneity of the distribution of dyes after the laser treatment is also confirmed by the quadratic tree decomposition parameters.
5. For two tested dyes, a change in the maximum reflectance of radiation in the range of 400-1000 nm was recorded after the laser procedure, which may indicate that the laser treatment may cause a change in the color of the dye.  
Conceptualization, M.K., B.K.-S., A.B. and W.P.; methodology, B.K.-S., M.K., A.B., M.H.-P., R.K. and W.P.; software, R.K. and M.H.-P.; validation, A.B., R.K. and K.J.; formal analysis, A.B., M.K. and B.K.-S.; investigation M.K., B.K.-S. and W.P.; resources, S.W.; data curation, M.K., B.K.-S., K.J. and W.P.; writing--original draft preparation, M.K., B.K.-S., W.P., A.L. and M.H.-P.; writing--review and editing, M.K., B.K.-S., A.B., A.L. and S.W.; visualization, A.B., K.J. and M.H.-P.; supervision, S.W.; project administration, A.B.; funding acquisition, S.W. All authors have read and agreed to the published version of the manuscript.  
This research was funded by the Medical University of Silesia, University Funds.  
The study was conducted in accordance with the Declaration of Helsinki and approved by the Bioethics Committee of the Medical University of Silesia (PCN/CBN/0022/KB1/27/III/16/17/21).  
Informed Consent Statement: Informed consent was obtained from all subjects involved in the study.  
The datasets used and/or analyzed during the current study are available from the corresponding author on reasonable request.  
The authors declare no conflict of interest.
# A Bilateral Craniectomy Technique for In Vivo Photoacoustic Brain Imaging
## 1 Introduction  
Craniotomy is a method for surgically opening or removing the skull of a subject to expose the brain for experimental procedures. Over the last two decades, a lot of work has been carried out to make craniotomy procedures safer for the subject and easier to implement and to provide better visual aid of the brain. During a craniotomy procedure, a section of the skull is lifted or taken out to reveal the brain underneath. Due to their thin, translucent skulls and less opaque cortical tissue, mouse models are frequently employed to assess the effectiveness of optical brain imaging techniques [1, 2]. These features enable sufficient light penetration, making mice a suitable choice for such evaluations [3, 4]. Lately, there has been a surge in interest in rat brain imaging, primarily driven by the emergence of transgenic rats. These genetically modified rats offer a valuable platform for investigating the underlying pathophysiology of complex behavioral and cognitive conditions [5]. Rat skulls, however, are much thicker (0.6\(-\)1.1 mm in rats versus 0.4-0.7 mm in mice depending on the specific strain of the animal and their age) [6]. Performing surgery on rat skulls to expose the brain presents inherent challenges, including risks of cortical bleeding, exposure of the pial surface to the external environment, inflammation, and potential distortion of the brain tissue and vascular structure due to edema [1]. Moreover, there is a risk of mechanical damage to underlying tissue while drilling through a thicker skull surface. Most of the current craniotomy techniques can only create a small window (\(-\)4-5 mm diameter) to expose the brain [7, 8, 9, 10, 11], which are limited to unilateral exposure due to the presence of the superior sagittal sinus as a midline structure. Newer models have been devised, involving thinning or excision of the bone flap and the insertion of a transparent cover, enabling prolonged observation of the brain. However, these craniotomies also remainrelatively small, measuring up to 7 mm in size [1, 12, 13, 14, 15, 16, 17]. As a result of these challenges, the rat craniomy approach has become limited, impeding the achievement of optimal visualization of cortical structures. This limitation, in turn, restricts the comprehensive understanding of neural processes and may also hinder the complete evaluation of optical brain imaging modalities.  
In this study, our aim is to present a comprehensive guide for a new bilateral hemicraniectomy technique in rat models. This innovative method allows for complete exposure and visualization of the rat brain in vivo, utilizing optical imaging techniques. To validate the efficacy of our approach, we employed a photoacoustic microscopy imaging system to capture high-resolution images of the brain region, covering a diameter of 15 mm.
## 2 System Overview
### Multimode Digitally Reconfigurable Radar System
Flipping the bias states at the same time inverts the phase of the output and achieves the desired binary performance. In this design, MACOM MADP-000907-14020P PIN diodes with switching times of 2 ns were used, allowing the BPS to modulate the carrier signal phase up to 10 GHz if needed. This BPS has an operating bandwidth of 5.72 GHz centered on 24.74 GHz, which covers the radar system's design bandwidth and has an absolute phase difference greater than 170\({}^{\circ}\) between the states across this bandwidth. The insertion loss across this bandwidth is less than 5 dB, and the input matching is less than \(-\)15 dB. The passive quadrature mixer used in this radar design is adapted from [40]. It consists of two balanced mixers, each made with a 90\({}^{\circ}\) hybrid coupler and two Skyworks SMS7621-060 Schottky diodes. The mixer uses the unmodulated carrier split by another 90\({}^{\circ}\) hybrid coupler as the local oscillator (LO) input and the modulated RX signal reflected off the target split by a Wilkinson power divider as the RF input. This arrangement mixes the LO and RF to downconvert the RX signal to low-frequency baseband signals that contain only the modulation and target information. This way, the 90\({}^{\circ}\) phase difference for the desired \(I\) and \(Q\) responses for target distance null-point removal is achieved and various \(I/Q\) processing methods are possible, such as arctangent or linear demodulation. The VCO chosen to feed into the SMA connector is an Analog Devices HMC739 operating at a carrier frequency \(F_{\text{C}}\) of 24.125 GHz and has a total frequency range of 23.8 to 26.8 GHz. All passive structures were designed with operating bandwidths of at least 4 GHz centered at \(F_{\text{C}}\). The 4 \(\times\) 4 patch antenna array was chosen for the high directivity to reduce multipath and off-axis interferences, as well as the high gain. It is also planar, easy to fabricate, and straightforward to integrate into the radar using microstrip waveguides. The Wilkinson power dividers used for splitting the VCO to the BPS and \(I/Q\) channels of the mixer have an S21 and S31 equal power split of \(-\)4 dB along with better than \(-\)10 dB input matching at all ports across the operating bandwidth. The \(I/Q\) channels are fed through identical AC coupled baseband amplifiers and combined to form the complex \(I/Q\) response \(I+jQ\).
## 3 Results and Discussion  
### Experiment 1: Optimum Training Sample Size  
In this experiment the sample size of the training data, set to 10% up to 50% without considering missing data and only spectral bands of eight images captured on path 162, without their gradient and VIs, are used for classification. The RF classification is performed with 15 times replacement and with 50 trees (forest size) in case 1. The averages of the overall accuracy (OA) and kappa coefficient [47] are computed and provided in Figure 6.  
\begin{table}
\begin{tabular}{c c c} \hline \hline \multicolumn{2}{c}{**Experimental Setup**} \\ \hline
**Forest size (\# of trees)** & 10–1000 \\
**Training sample size** & 10–50\% \\
**Missing data** & Yes & No \\
**VIs** & Yes & No \\
**Temporal gradient of VIs and spectral bands** & Yes & No \\
**\# of images** & 1–10 \\ \hline \hline \end{tabular}
\end{table}
Table 4: The different scenarios for the RF classification.  
\begin{table}
\begin{tabular}{c c c} \hline \hline
**Case** & **\# of Classes** & **Desired Classes** \\ \hline
1 & 3 & wheat, barley, other \\
2 & 2 & (wheat and barley), other \\ \hline \hline \end{tabular}
\end{table}
Table 5: Two cases of classification.  
With an increasing training sample size, the OA and the kappa coefficient are improved (Figure 6). This improvement is not remarkable when the training sample size becomes more than 30%. Hence, we selected 30% as the appropriate training size due to the cost of fieldwork.
# Using a Cable-Driven Parallel Robot with Applications in 3D Concrete Printing
###### Abstract  
In construction, a large-scale 3D printing method for construction is used to build houses quickly, based on Computerized Aid Design. Currently, the construction industry is beginning to apply quite a lot of 3D printing technologies to create buildings that require a quick construction time and complex structures that classical methods cannot implement. In this paper, a Cable-Driven Parallel Robot (CDPR) is described for the 3D printing of concrete for building a house. The CDPR structures are designed to be suitable for 3D printing in a large workspace. A linear programming algorithm was used to quickly calculate the inverse kinematic problem with the force equilibrium condition for the moving platform; this method is suitable for the flexible configuration of a CDPR corresponding to the various spaces. Cable sagging was also analyzed by the Trust-Region-Dogleg algorithm to increase the accuracy of the inverse kinematic problem for controlling the robot to perform basic trajectory interpolation movements. The paper also covers the design and analysis of a concrete extruder for the 3D printing method. The analytical results are experimented with based on a prototype of the CDPR to evaluate the work ability and suitability of this design. The results show that this design is suitable for 3D printing in construction, with high precision and a stable trajectory printing. The robot configuration can be easily adjusted and calculated to suit the construction space, while maintaining rigidity as well as an adequate operating space. The actuators are compact, easy to disassemble and move, and capable of accommodating a wide variety of dimensions.  
Cable-Driven Parallel Robot; 3D concrete printer; mortar extruder; kinematic; static workspace of CDPRs +
Footnote †: journal: Applied Sciences
## 2 Materials and Methods
### Bonding Properties Evaluation Index  
The bonding properties of the PE\(-\)ECC specimen's fiber and matrix were evaluated using the deformation energy set uniaxial tensile test proposed in the literature [50]. The elastic stage of PE\(-\)ECC was the first stage, the transition from the elastic stage to the strain\(-\)hardening stage was the second stage, and the strain\(-\)hardening stage was the final stage. The bonding strength and the average number of cracks were used to evaluate the bonding properties of PE\(-\)ECC. The formulas for calculating the PE\(-\)ECC's bonding properties index are shown below.  
(1) Formula for bond strength calculation  
The deformation energy was substituted into the stress formula, and the difference between the ultimate load deformation energy and the crack load deformation energy was used to determine the bonding effect as shown in Equation (1):  
\[\tau=\frac{U_{s}-U_{c}}{\tau d_{f}L_{f}(u_{s}-u_{c})} \tag{1}\]  
where \(d_{f}\) is the fiber diameter, \(L_{f}\) is the fiber length, \(U_{s}\) is the maximum deformation energy in the softening phase and the deformation energy in the third stage of the corresponding load\(-\)displacement curve, \(U_{c}\) is the matrix cracking deformation energy, \(u_{s}\) is the maximum displacement in the softening phase, and \(u_{c}\) is the matrix cracking displacement.  
(2) Formula for average crack number  
Under the energy criterion of fracture mechanics, the average number of cracks was determined by dividing the total energy number by the energy of a crack, and the cracking effect caused by the bond failure between the fiber and matrix of the ECC tensile test piece was evaluated as shown in Equation (2):  
\[n=\frac{U_{s}-U_{fc}}{U_{fc}+\frac{ku_{fc}}{2}} \tag{2}\]  
where \(U_{fc}\) is the total deformation energy of the first and second stages, \(U_{s}\) is the maximum deformation energy in the softening phase, \(ku_{fc}{}^{2}/2\) is the modification of the strain\(-\)hardening stage to the previous stage, \(u_{fc}\) is the displacement of the second stage of the curve, and \(k\) is the slope of curve fitting in the third stage.
# Low-Power Two-Phase Clocking Adiabatic PUF Circuit
## 2 Fundamental Adiabatic PUF
### Proposed Adiabatic PUF
#### 2.3.2 Theoretical Analysis of the Proposed Adiabatic PUF  
In most of today's CMOS processes, the PMOS devices are physically separated from each other by fabricating in an n-well [33]. This facilitates individual connection between the bulk and source of each PMOS device. Accordingly, we have investigated the body effect of a PMOS by connecting the body of a PMOS to Vdd (constant voltage) of the Vpc power clock, and to the source of each PMOS (P1, P2, and P3 in Figure 3a). Figure 5 shows the output signals (response bit Rb signals) of the proposed adiabatic PUF versus the QUALPUF circuit. As labeled in Figure 5a,b, (BS): PMOS bulk is tied to each respective Source, (Vpc): all PMOS bulks are tied to Vpc signal, and (Vdd): all PMOS bulks are tied to constant Vdd. The circuit operation is shown in Figure 4. Let \(\mathrm{Cb}=0\). Then, P1 and P2 are ON, and \(\mathrm{C_{L}}\) is charged from Vpc (the RC model in Figure 4b, and such signal is shown at \(\mathrm{t}=0.15\)-\(0.2\) us, as shown in Figure 5). In contrast, Figure 4c illustrates that when \(\mathrm{Cb}=\mathrm{Vdd}\), P2 and N1 are ON, forcing CL to discharge to ground level (such signal is shown at \(\mathrm{t}=0.1\)-\(0.15\) us, as shown in Figure 5). We attempted here to reduce the output voltage level of Rb (Figure 4c) as close to zero as possible (when challenge bit \(\mathrm{Cb}=1\), i.e., \(\mathrm{Cb}\) logic \"1\" or Vdd). However, the response bit Rb cannot be declined to ground because of a voltage drop at RP2, which is associated with the VTH of PMOS P2. The MOS VTH variation is expressed as follows:  
\[\mathrm{V_{TH}}=\mathrm{V_{TH0}}+\gamma(\sqrt{|2\Phi\mathrm{F}+\mathrm{V_{SB} }|}-\sqrt{|2\Phi\mathrm{F}|}) \tag{8}\]  
where \(\gamma\) and \(\Phi\mathrm{F}\) are MOSFET device parameters, and VSB is the source-bulk potential difference [34]. In our proposed PUF design, the PMOS body is connected to its source pin, as shown in Figure 4a,c, indicating that VSB = 0 V; hence, the VTH of P2 is \(\leq\)VTH0, which is the lowest output voltage level, as depicted in Figure 5. Therefore, the bulk of PMOS that is tied to each source is chosen for further simulations.  
Figure 4: Proposed adiabatic PUF; (a) active transistors during charging and discharging the response node, (b) RC equivalent model at \(\mathrm{Cb}=0\) V, and (c) RC equivalent model at \(\mathrm{Cb}=1.8\) V.  
Figure 5: Evaluation result of challenge bit under the PMOS transistor body effect. PMOS bulk: tied to source (labeled as BS: body to source), tied to Vpc (labeled as Vpc) and tied to Vdd (labeled as Vdd).
# Impact of Cubic Symmetry on Optical Activity of Dielectric 8-srs Networks
## 2 Materials and Methods  
### Galvo-Dithered Direct Laser Writing  
The 8-srs PhCs were fabricated using a GD-DLW system (Figure 2b). The GD-DLW setup consists of illumination with a frequency doubled femtosecond laser (Coherent Fidelity 2) with an operating wavelength of 535 nm. Pulse width is 55 fs and repetition rate is 70 MHz. Power of the laser beam is controlled electronically using a rotating half-wave plate and linear polarizer. A mechanical shutter is used to control light exposure during fabrication. The most important addition to the GD-DLW setup is the introduction of two computer-controlled galvo-mirrors, electromechanical instruments that deflect a light beam with a mirror on receipt of an electronic signal. Using galvo-mirrors, the angle of the laser beam is modulated and steered into an oil immersion objective (100X, 1.4 N.A., Olympus, Tokyo, Japan) using a 4-f imaging system. Radius of the dithered correction, R, is comparable to the voxel resolution. This causes the fabrication voxel to become larger in lateral directions and shorter in the axial direction, improving overall resolution of the 3D fabrication method and leading to a correction of voxel asymmetry. A piezoelectric nano-translation stage (Physik Instrumente, Karlsruhe, Germany) mounted on a stepper motor controller (Thorlabs, Newton, NJ, USA) was used to trace out microstructures in a photoresist. A zirconium-based hybrid organic-inorganic photoresist was used to create templates due to its excellent resistance to shrinkage [38]. GD-DLW of 3D microstructures starts by writing the top unit cell layer to ensure the laser passes through a homogeneous material, as the fabrication system is in an inverted configuration. The bottom layer is intentionally written 3 \(\upmu\)m below the glass-polymer interface to ensure the microstructure will be attached to the glass coverslip over the entire area of the microstructure. Failing to do this procedure may result in the microstructure being written entirely within the polymer and being lost during the wash out process. After the GD-DLW procedure, the sample is rinsed in a 1-Propanol:2-Propanol (30:70) solvent mixture for 60 min and then dried at room temperature.  
Figure 2: Galvo-dithered direct laser writing (GD-DLW) system. (**a**) Illustration of circular dithered correction applied by galvo-mirrors. Radius of the dithered correction, R, is comparable to the voxel resolution. This causes the fabrication voxel to become shorter in the Z direction, improving overall resolution of the 3D fabrication method and leading to correction of voxel asymmetry. (**b**) Schematic of the GD-DLW setup.
# Numerical Modeling of Non-Uniformly Reinforced Carbon Concrete Lightweight Ceiling Elements
## 5 Finite Element Simulation of the Carbon Concrete Girder  
Finite element model of the tested girder described in Section 1 has been decomposed into twelve zones to account for the different cross-sectional layups as shown in Figure 16. Sections 4-12 correspond to the reinforced sections displayed previously in the technical drawing in Figure 4. In addition to the reinforced sections, the finite element model also includes the non-reinforced boundary sections 1-3 positioned behind the supports.  
Figure 16: Cross sections of the girder with the corresponding layouts described in Tables 2 and 3.  
Figure 15: Development of strain and strain profiles of the carbon concrete beam with cross section (ii) according to Figure 14.  
The finite element discretization with the twelve sections is displayed in Figure 17. The finite element type was a bilinear quadrilateral layered shell element with three translational and two rotational degrees of freedom at each node. In the applied _ABAQUS_ code, this element is referred to as a _conventional_ shell element [31]. This type of element provides the possibility to define several layers within the cross section that can be associated with different material models and material parameters. This feature has been utilized to combine the microplane damage model for the concrete layers and the explicitly defined bilinear stress-strain curves for the fabric layers in a single cross section.  
The symmetry of the shell was exploited to reduce the size of the simulated structure to a half of the girder. The load was introduced using displacement-control using stiff plates at positions indicated in Figure 17. To introduce the load from the plates to the shell consistently with the test setup, a frictionless contact was defined between the plates and the girder surface. The deflection of the girder was measured at the mid-span on the bottom side of the girder.  
The described finite element model was used to study the effect of the cross section representation using four versions of cross section representation (i-iv) displayed in Figure 18. The simulated load-deflection curves corresponding to the four versions of the model are plotted in Figure 19 together with the test result. The obtained response curves are discussed in detail in the following sections.  
Figure 17: Finite element model of the lightweight girder: (**a**) finite element mesh and (**b**) dimensions of the girder cross section.  
Figure 18: Studied types of cross-sectional representations (i–iv).