## 4 Simulation and Experiment Analysis  
The designed multi-output forward converter with weighted control demonstrates better cross-regulation and efficiency. A suitable prototype was developed based on the design discussion in the previous discussion, and its testing is described in this section. We designed our circuit using the weighted average method on 15 V and 12 V outputs. Tables 9 and 10 show the voltages occurring in the output voltage at various loads, according to the input voltage. Precise measurements were made using an electronic load. It is clear how stable these voltage changes remain. It can be observed that the voltage change for the 3.3 V output is greater than for the other outputs in percentage. The reasons why this third output (3.3 V) has more voltage change are as follows. 1. In the multiple-output forward converter, the information of voltage value for this winding was not received. 2. The current passing through the diode in its winding always changes under different loads. 3. The internal resistance on the transformer of the winding is proportionally different to the resistance in the other windings. 4. The secondary winding to which it is connected causes voltage changes due to common inductance. 5. When designing the transformer winding, the obligation of making a half winding or full winding causes voltage value changes. 6. Primary and secondary windings can never be perfectly coupled. There is leakage inductance between the windings. \begin{table}
\begin{tabular}{c c c c c c c c c} \hline \hline  & & **3.3 V** & & **12 V** & & **15 V** & \\ \hline
**Load** & **Load** & **Voltage** & **Pout** & **Load** & **Voltage** & **Pout** & **Load** & **Voltage** & **Pout** \\
**(\%)** & **(A)** & **(V)** & **(W)** & **(A)** & **(V)** & **(W)** & **(A)** & **(V)** & **(W)** \\ \hline
10\% & 0.2 & 3.41 & 0.68 & 0.2 & 12.04 &  
In fact, if we had not created a 3.3 V third winding in our design, and had only taken the voltage values from the fist and second outputs in our design, then the cross-regulation would be expected to be only \(\pm\)0.33%. This shows us how high-quality the design is. In other words, this proposed study proves its quality under certain loads in terms of good cross-regulation. Figure 7 shows the voltages obtained at the output. These images show the quality of the output voltages. Also, even if the output is not filtered, the worst ripple on the outputs is around 20 mV. Less rippled voltages were obtained by using an extra filter on the 12 V and 15 V outputs. In this case, the ripple voltage is mitigated to less than 1%. We should also point out that since electronic load was used, precise measurements were taken. Figure 8 shows the V\({}_{\text{DS}}\) voltage at 50 V underfull load and 80 V under full load. At 80 V under full load, the maximum peak voltage is approximately 250 V. Since the integrated circuit used has a drain-source breakdown voltage of 800 V, it works flawlessly. As can be seen from Figure 9, there is a 200 mV jump during the transition from full load to 50% load at the 15 V output voltage, which has a jump rate of 1.33%. Figure 9 shows the initial transition at full load with an output voltage of 15 V. These show us the dynamic behaviour of the control. The results are exactly as we expected. It can also be seen from Figure 9 that the phase margin is 68.9\({}^{\circ}\). The results are exactly as we expected. Figure 8: (a) V\({}_{\text{DS}}\) voltage at 50 V underfull load of designed forward converter with weighted control; (b) V\({}_{\text{DS}}\) voltage at 80 Vunderfull load of designed forward converter with weighted control. Figure 7: (a) 50 V under full load of designed forward converter with weighted control; (b) 80 V under full load of designed forward converter with weighted control. Figure 10 shows the current waveforms of the proposed converter at 80 V under full load. These current waveforms match the waveforms shown in the circuit description.