esa-sceva/satcom-chunk-collection huggingface dataset:
## 2 Material and Methods
### Data Collection  
Data collection was performed using 5 devices simultaneously: Qualisys motion system (QMS), from Qualisys AB-Goteborg-Sweden, Force platform (FP), from Bertec FP6090, Ergojump (E)), jump mat device from Junghans GMBH-Schramberg-Schramberg-Germany, Myotest Pro (MP), triaxial acceleration measurement device from Myotest(r) Inc.--Sion, Switzerland, and self-made Abalakow belt jump (ABJ).  
QMS employed 12 infrared cameras to capture kinematic data at a sample rate of 200 Hz, with a spatial resolution of 1 mm, and calibrated following manufacturer guidelines. Two reflective markers with 12 mm diameter were placed over the left and right lateral femoral condyles to measure jump height. This was done for three purposes, (a) to be as close as possible to the whole-body centre of mass [25], (b) to avoid tracking displacements in the sagittal plane associated with trunk flexion, and (c) to track predominantly the vertical position of the whole-body centre of mass.  
The FP measured ground reaction force at 2000 Hz and was hardwire synchronised with the data acquisition of the QMS. All jumps were performed from an EJ mat placed on top of the force platform, with jump height automatically calculated by the device.  
The MP device incorporated a tri-axial accelerometer to measure the global acceleration and was fixed to the left side of the pelvis at the level of the left lateral femoral head with a Velcro elastic belt shown in Figure 1. Data were sampled at 200 Hz, stored in the device, and post-processed using manufacturer software.  
The ABJ involved an inelastic tape passed through a floor-level roller attached to a board placed above the jump mat. The tape is attached to the waist belt and can freely pass through the floor level roller. As a participant jumps, the excess tape passes through the roller, and it is the difference in the tape length pre and post jump that is used as jump height.  
For data collection, participants stood with straight legs upon the EJ mat, ABJ plate, and FP with the EJ and ABJ fixed to the FP with double-sided tape (Figure 1). Then, holding hands on their hips, starting in an upright standing position, they would perform a jump beginning with a countermovement down to a knee angle of approximately 90 degrees,  
Figure 1: Vertical jump test.  
with take-off and landing always in the same position (with straight legs and plantarflexed ankles). The ABJ sliding tape was made taught between belt and floor whilst standing. The standard jump protocol of the MP system required five consecutive jumps to be performed after a starting signal with a five seconds interval between jumps. To overcome this software limitation, avoid fatigue, and be able to compare measurements obtained from the five devices, participants performed the highest jump as the first in the sequence of five and then undertook four submaximal jumps after this. Only the first jump in this sequence was used for the evaluation of devices. The participants repeated this procedure twice with a 40 s recovery in between to obtain three maximal height vertical jumps.
## 4 Mathematical Modeling
### Modeling the Angle of Arrival (AoA) and the Total Antenna Gain as a Function of the AoA  
As assumed previously, the flying platform is assumed to be unable to rotate along its longitudinal axis. On the other hand, its longitudinal axis is tangential to the flight profile. Therefore, the mathematical derivation of the flight profile yields the values within which the E-plane and H-plane radiation patterns of the onboard GNSS antenna should rotate. As these radiation patterns correspond to the \(XZ\) and \(XY\) planes, it is sufficient to calculate the slope with respect to just two out of the three axes. Hence,  
\[\theta_{Y}=\tan^{-1}\biggl{(}\frac{z(x)}{\partial y(x)}\biggr{)} \tag{5}\]  
\[\theta_{Z}=\tan^{-1}\biggl{(}\frac{z(x)}{\partial x}\biggr{)} \tag{6}\]  
In addition, given that the _Source_ can be located anywhere in the 3D space around the landing site, it can be logically justified to assume it to be located at any desired altitude (\(h_{TX}\geq 0\)). The line-of-sight (LoS) vector can then be translated from the landing site position to the _Source_ position. Thus,  
\[\begin{array}{l}\par\par\par\par\par\par\par\par\par\par\par\par\par\  
In (9), the [..] operator represents the floor function. The corresponding gains in the E- and H-planes are therefore \(g_{zy}(AoA_{zy})\) and \(g_{zx}(AoA_{zx})\), respectively. Finally, the final antenna gain in the direction of the received signal can be calculated as follows:  
\[G\big{(}AoA_{zx},AoA_{zy}\big{)}=\begin{pmatrix}(g_{zx}(AoA_{zx})\sin((AoA_{zx}) )^{2}+\\ (g_{zy}(AoA_{zy})\sin(\big{(}AoA_{zy})\big{)}^{2}+\\ (g_{zx}(AoA_{zx})\cos((AoA_{zx}))^{2}\end{pmatrix}^{1/_{2}} \tag{10}\]
## 2 Related Works
### Routing Based on Social Networks  
By the abovementioned routing schemes, good performance may not be obtained in some DTNs which have the characteristics of social networks and it has been proven in the following references. Existing studies show that in such scenarios, there are some active nodes which can transmit messages to their destinations with less hops. For example, in a campus scenario, students in the same group contact frequently while students in different groups have less contact, but a group leader has more contacts between different groups. Some new schemes have been proposed to address routing issues in such DTNs. In [12] the application of these characteristics to communication systems have been highlighted. In [13], the authors have derived the optimization of the routing policy in such social DTNs. In [14], based on the small world theory, a routing algorithm has been proposed to combine the concepts of similarity and centrality, where the similarity refers to the number of the same neighbors of two nodes while the ratio of the number of the shortest paths including a node over the number of all the shortest paths is defined as the centrality of the node. Additionally, in [15] in accordance with the two important characteristics of a social network, community and centrality, the authors have proposed a forwarding algorithm, by which messages will be constantly forwarded to the nodes with the higher centrality since these nodes will have higher probability to meet the destination node of the messages. Similar works can also be found in [16,17]. More social characteristics such as the social distance defined in [18], the asynchronous centrality defined in [19], the social links of the nodes pairs defined in [20], the node's social relation defined in [21], the impact of strangers defined in [22] and the group movement defined in [23] can be employed to make the forwarding decision. A more efficient combination of the social features of the mobile nodes and the relationship among them is expected to achieve much better performance.
# Laser Technology in Photonic Applications for Space
## 2 Laser Devices
### Solid State Laser (SSL)  
In this review, most of the SSLs that we will discuss are pumped by semiconductor diode lasers (DPSSL). SSL present several advantages over semiconductor laser, such as beam quality and the possibility to allow for extra versatility by reaching wavelengths and/or output powers which are not easily achieved by semiconductor lasers. In addition, short pulses can be emitted, for instance, through Q-switching, which are commonly used in range-finding applications. The space applications in which DPSSL lasers are used include Light Detection and Ranging (LIDAR) and spectrometer devices. An example of the former application would be the GEDI (Global Ecosystems Dynamics Investigation Lidar) instrument, developed for NASA's Earth Venture Instrument (EVI) space program, which uses a version of the High Output Maximum Efficiency Resonator (HOMER) laser, an Nd:YAG crystal side-pumped by seven, 4-bar G-package laser diode arrays ([PERSON] et al., 2018). An example of the latter application would be the ESA/ROSCOSMOS ExoMars 2020 mission to Mars, that includes a Raman Laser Spectrometer (RLS) instrument whose excitation source is an intracavity frequency-doubled DPSSL emitting at 532 nm, shown in Figure 1, pumped by a CW (continuous-wave) Q-mount diode emitting at 808 nm ([PERSON] et al., 2018).
## 5 Simulation Results
Regarding the rotor current shown in Figure 12, for the inductive FCL placed in the rotor side, the rotor fault current level in the steady state of the fault was less than the other FCL locations, due to the high leakage coefficient value shown in Figure 5b. This point has been discussed in Section 4.1. The impacts of the resistive type FCL for the three locations are shown in Figure 13. As mentioned, the operation of the FCL with resistive impedance in the stator side was the most effective one in limiting both the stator and rotor currents level. The resistive impedance in the stator side was capable of compensating for the voltage sag in the DFIG terminal, and was also able to absorb excess active power during the fault condition. For the FCL at the terminal side, its impact was almost the same as the FCL placed at the stator side. Regarding Figure 12, due to decreasing the RSC controllability by employing the FCL at the rotor side, there was a high current level in both the stator and rotor sides. However, in order to achieve a good fault current limitation in the rotor side by the FCL, a high impedance value should be employed in the FCL, either in the inductive type FCL or the resistive type FCL. Considering the results provided for the rotor and the stator currents, the inductive FCL almost had the same impact on the stator current and the rotor current regardless of its location. However, it should be noted that the FCL located in either the stator side or the terminal side had the capability of compensating for the voltage sag in the terminal of the DFIG as well as increasing the RSC controllability. The resistive FCL was most effective in enhancing the FRT capability of the DFIG if it was located in the stator side or the terminal side. Like the inductive FCL, located in the stator or the terminal sides, the resistive FCL could compensate the voltage sag in the terminal and increase the RSC controllability. But, the resistive FCL, located in the stator side or the terminal side, compared to the inductive FCL, located in the stator side or the terminal side, was able to consume excess active power during the fault condition. In fact, from the FRT capability enhancement point of view, the resistive FCL placed in the stator or the terminal sides had the best operation. Figure 12: With the inductive type fault current limiter in the stator side (L1), in the terminal side (L2), and in the rotor side (L4) during a three-phase fault: (**a**) The stator currents; and (**b**) the rotor currents.
# A Review of High-Sensitivity Tracking Techniques for Satellite Navigation Signals
###### Abstract  
With the increasing demand for high-sensitivity signal tracking in complex environments, GNSS receiver technologies have continuously evolved in both architecture and algorithmic design. This paper presents a systematic review of the development of high-sensitivity tracking techniques, with a focus on the transition from closed-loop to open-loop, hybrid, and deeply integrated architectures. Key strategies--such as coherent integration time extension, discriminator and loop filter optimization, vector tracking (VT), and Direct Position Estimation (DPE) are evaluated in the context of weak signal scenarios. To address the limitations of existing methods, including strong dependence on filter models, oscillator instability, and computational complexity, this study also outlines future research directions, including (1) integrating deep learning techniques into filter structures to enhance adaptability and robustness; (2) developing multi-channel collaborative estimation schemes to mitigate oscillator noise in weak signal environments; and (3) designing low-complexity open-loop tracking approximations to align with hardware resource constraints. Thus, enhancing the necessity of navigation continuity and robustness under low-signal-to-noise-ratio (SNR) conditions.  
high-sensitivity tracking; closed-loop tracking; open-loop tracking; direct position estimation (DPE)
# Optical Beamforming Networks for Millimeter-Wave Wireless Communications
## 2 Principles
### Principle of TTD Architectures  
As presented in Figure 2, TTD architectures utilize the direct detection of modulated optical carriers, in which the signal processing of a channel is as follows. The optical carrier from a laser is modulated by a RF signal, which is then delayed by a TTD with a time delay of \(\Delta t\), then the optical carrier is fed to PD and mixed back to RF signal. The other channels have a similar operation with the optical carrier and generate a group of RF signals with a fixed phase difference, in order to form a beam with a certain angle.  
Figure 1: Schematic diagrams of PAAs using OBFNs: (**a**) a 1D PAA and (**b**) a 2D PAA.  
Figure 2: Operation of the RF signal in one channel of a TTD architecture with non-coherent optical carriers.  
Ignoring the high-order harmonics, the optical signal before the PD can be expressed as follows: [30]  
\[S(t)_{1}=A_{1}\text{exp}^{\text{i}(2\pi f_{1}(t+\Delta t))}+A_{2}\text{exp}^{ \text{i}(2\pi(f_{1}+f_{\text{RF}})(t+\Delta t)+\phi_{0})}-A_{2}\text{exp}^{ \text{i}(2\pi(f_{1}-f_{\text{RF}})(t+\Delta t)+\phi_{0})} \tag{5}\]  
where \(A_{1}\) and \(A_{2}\) are the amplitude of the optical carrier and sidebands, \(\Delta t\) is the time delay, and \(\phi_{0}\) is the initial phase of the RF signal. Detected by the PD, an electric current is produced as follows:  
\[I(t)_{1}=R|S(t)_{1}\times S^{*}(t)_{1}| \tag{6}\]  
where \(R\) is the responsivity of PD. Neglecting components of the direct current and beating term, the electric current can be written as follows:  
\[I(t)_{1}=R[4A_{1}A_{2}\text{cos}(2\pi f_{\text{RF}}(t+\Delta t)+\phi_{0})] \tag{7}\]  
This equation states that the phase of the RF signal is shifted by \(2\pi f_{\text{RF}}\Delta t\).
# Ground-Borne Vibration Model in the near Field of Tunnel Blasting
## 1 Introduction
The prediction effect of this formula in the near field of blasting is also unsatisfactory, but due to its simple calculation, it is still widely used as a trend analysis rather than for accurate prediction in many engineering practices. Following the above-mentioned work, this paper first discusses the shortcomings of the Sadovsky formula at the mathematical level, then considers the influence of various factors on blasting vibration with their mutual influence and deduces a prediction model of peak particle velocity through dimensional analysis. Then, this model and the Sadovsky formula [14] are utilized to predict the vibration velocity as a comparative analysis based on the vibration data of near-field blasting collected from a small-spacing tunnel at Badaling station of Beijing Zhangjiakou high-speed railway. On this basis, variance analysis and Akaike information criterion are used to evaluate the advantages of the new model compared with the traditional model in terms of prediction accuracy and application scope, as well as its uniqueness in dealing with the impact of changes in geological conditions, cavity effects, and the number of free surfaces.
# Selective Extraction of REEs Thanks to One-Pot Silica Hybrid Materials
## 3 Results and Discussion  
### Materials Characterization  
Before beginning the extraction experiments, the obtained silsesquioxanes were characterized. First, the material composition was examined using FT-IR and TGA. All FT-IR spectra (Supplementary Materials Figure S1) show characteristic peaks at 3130 cm\({}^{-1}\) assigned to the C-H stretching mode of the triazole moiety, at 2920 cm\({}^{-1}\) and 2850 cm\({}^{-1}\), which are attributed to the CH\({}_{2}\) asymmetric and symmetric stretching modes, at 1460 cm\({}^{-1}\), which is assigned to the C = C stretching in the triazole moiety, at 1210 cm\({}^{-1}\), which is assigned to the Si-CH\({}_{2}\)- stretching mode, and at 1020-930 cm\({}^{-1}\), which is attributed to the Si-OH stretching modes [31; 32; 33]. The presence of the triazole moiety and the conservation of the Si-C bond is therefore confirmed in all final materials. Additionally, the presence of the functional headgroup was confirmed from their characteristic peaks, such as a signal at 1660 cm\({}^{-1}\) assigned to the N-H bending mode of the primary amine for SHM-2. The C = O stretching mode from the carboxylic acid was observed at \(\sim\)1720 cm\({}^{-1}\) for SHM-3, while strong transmittance bandswere observed at \(\sim\)1650 cm\({}^{-1}\), corresponding to the amide C = O stretching frequencies [34] of the diglycolamide for SHM-4 (the etheric C-O stretching at 1110 cm\({}^{-1}\) was not detected due to the presence of the strong Si-O-Si signals). For SHM-5, the C = O stretching mode at \(\sim\)1740 cm\({}^{-1}\) was attributed to the ester, and \(\sim\)1690 cm\({}^{-1}\) was assigned to amide carbonyl stretching [35].  
Hence, the material structure is validated in the form displayed in Figure 2. After heating to 130 \({}^{\circ}\)C for 24 h, the intensity of the peak between 1020 and 930 cm\({}^{-1}\) significantly decreased in favor of an intensity increase of the Si-O-Si peaks. This indicates the progression of the material condensation.  
Using TGA (Figure S2), the molecular weight of the silsesquioxane (\(M_{TGA}\)) was calculated by the equation \(M_{TGA}=\frac{100}{w_{700}\cdot\mathrm{C}}\ast M_{\mathrm{SiO_{2}}}\), where \(M_{\mathrm{SiO2}}\) is the molecular weight of silica (60.09 g mol\({}^{-1}\)) and \(w_{700}\cdot\mathrm{C}\) is the constant residual weight percentage of the corresponding material. The results are shown in Table S1. The validity of this equation has been ensured by FT-IR results by verifying that the sample residue after TGA is pure silica.  
The calculated molecular weights are in good agreement with the theoretical values for a fully condensed silsesquioxane. A rather complete condensation is inferred. This agrees with the observations from FT-IR. For the extraction experiments, the obtained molecular weights are used to determine the required material mass.
# Therapeutic Potential and Challenges of Pioglitazone in Cancer Treatment
## 3 Therapeutic Use of Pioglitazone
### Therapeutic Effect on Different Types of Cancer
#### 3.6.6 Thyroid Cancer  
The use of pioglitazone has been correlated with neither increased nor decreased risk of thyroid cancer according to a study comprising mostly Eastern Asian individuals [88]. A widely studied finding is the PAX8-PPAR-\(\gamma\) Fusion Protein (PPFP) and how pioglitazone alters its function. PPFP is a result of a fused gene containing the significant majority of the Paired Box Gene 8 (PAX8) transcription factor, related to thyroid development and function, gene, and the entirety of the PPAR-\(\gamma\) gene and, as such, a binding site for TZDs [89]. As evident by the imminent intracellular lipid accumulation and the expression of adipocyte-related biomarkers upon treatment, pioglitazone induces the differentiation of thyroid cancer cells into adipocytes. Moreover, it is accepted that pioglitazone blocks the interaction between PPFP and Thyroid Transcription Factor 1 (TTF-1), which otherwise leads to the severe limiting of the differentiation induction by the former via the suspension of recruitment of synergistic molecules such as coactivators and corepressors [90]. Considering immunity, pioglitazone also advanced the infiltration of T cells and macrophages in the tumor microenvironment when tested on mice, and exhibited favorable properties in a clinical setting [91]. Unfortunately, [PERSON] et al. (2018), in their examination of 40 thyroid cancer patients, found that only one tested positive for PPFP, potentially indicating that it is a rare phenomenon in these cases [92]. Finally, studies have suggested that pioglitazone and metformin have a synergistic effect against thyroid cancer, especially in the induction of apoptosis [93].
## 3 Hardware Development
### Scheduling Module on Hardware  
The scheduling module is one of the core components required to achieve the multi-function characteristic of the designed SHM system. As PZT sensors are used as multi-functional sensors, they should be controlled by different circuits for different functions. The basic idea for achieving this is to adopt analog switches. These switches will guide the signal from the PZT sensors to different processing circuit parts according to users' demands.  
The architecture of this part is illustrated in Figure 2, and the corresponding scheme is shown in Figure 3. Two analog switches are employed: ADG 752 (Analog Devices Inc., Norwood, MA, USA), a single-pole, double-throw switch, and ADG728 (Analog Devices Inc., Norwood, MA, USA), an 8:1  
Figure 1: The architecture of the designed structural health monitoring (SHM) system.  
matrix switch. These two analog switches are controlled by a microcontroller unit (MCU) through an inter-integrated circuit (IIC) bus as detailed in Figure 3, where the arrowed line indicates the direction of signal flow.  
The ADG752 in Figure 3 serves as a mode selector. The S1 pin is connected to an impedance converter that generates an excitation signal for impedance measuring mode, while its S2 pin is connected to the ground for impact detecting mode. The microprocessor decides which pin will be connected to the D pin according to the chosen mode.  
If the impact detecting mode is selected, then the ADG752's S2 pin will be connected to the ADG752's D pin; therefore, one of the pins of each PZT sensors is connected to the same ground together, while the other pins are connected to charge amplifiers.  
For impedance measuring, the ADG752' S1 pin is connected to that of the D pin. The excitation signal will then flow into the PZT sensors. Next, the microprocessor will control the ADG728 to determine which PZT sensor will undergo impedance measurement by connecting a pin from S1 to S8 of ADG728 to its D pin. Further signal processing and calculation will be conducted in the impedance converter.