## 1 Introduction  
Complying with harmonic standards and power factor requirement of the input AC power has resulted in the development of boost power factor correction (PFC) circuits to get an improved power factor close to unity. Additionally, using interleaving PFC, numerous benefits are obtained, including an increased power density, reduced overall design volume, and declined RMS current flowing through the boost capacitor, and using an interleaved configuration leads to a significant decrease in the switching frequency ripples as a result of the ripple cancelation effect [1]. Notably, this application is employed to ensure sinusoidally shaped input currents in connection with differential mode (DM) electromagnetic interference (EMI) input filters, limiting the high-frequency noise transmission from the converter to the power grid [2]. However, the increased integration of power electronics converter into the grid results in some challenging EMI issues because of inherent pulse energy conversion characteristics. Thus, the unwanted emissions should be suppressed to fulfill noise emission standards, such as CISPR-11 for frequencies beyond 150 kHz [3]. Because of the increasing demand for pulse-width modulation (PWM) converters, a number of standards are defined below the frequency of 150 kHz in some applications, CISPR-14 (induction hubs) [4], and CISPR-15 (lighting equipment) [5]. Moreover, the CISPR 16-1-1 is split into two main frequencies as Band-A (9-150 kHz) and Band-B (150 kHz-30 MHz) [6]. An EMI estimation approach and EMI filter designing analysis are proposed for the 9-500 kHz based on the following assumptions:* DM noise estimation is only considered. A type of noise current is flowing in the same direction as the power supply current, known as \"DM,\" because the outgoing and return currents are reversely directed. * Rise time and fall time of switching waveform effects are ignored in the model. * DM EMI filter is analyzed from the volume optimization point of view. Analysis is not covering the common mode EMI filter volume optimization. * Parasitic component effects are negligible. EMI filter is effectively employed for reducing the EMI noise emissions, which is designed based on the required noise attenuation requirements. The EMI filter's dependency on the EMI noise's peak value has led to many modeling approaches to estimate the EMI noise peak in the Bands A and B frequency ranges [6; 7; 8; 9; 10]. Additionally, it is highly acceptable that the reduced grid input ripple current results in the reduction of the DM EMI noise magnitude and filter attenuation requirements, which make the DM EMI filter size smaller and the corner frequency higher [1]. So far, the EMI filter has been designed based on Band-B considering the presence of noise criteria within the frequency standards above 150 kHz [11]. Recently, Band-A has become important due to the advent of new standards. Notably, Band-A's design DM EMI filter provides enough damping in Band-B to shift the filter corner frequency within the low frequencies. In the past decade, higher efforts have been carried out to estimate the DM EMI noise emission. Additionally, most of the modeling approaches that have been focusing on EMI analysis within a frequency range above 150 kHz are based on simulations [7; 8]. Notably, prior state-of-the-art simulation-based methods may be quite cumbersome if scaled up for system-level studies. Only a few analytical-based approaches are introduced for differential mode noise as in [9] to EMI filter designing based on the input current ripple equation of the interleaved boost PFC. It is only suitable for EMI filter designing for conventional phase shift interleaved and frequency above 150 kHz. Analytical DM EMI estimation is proposed for non-interleaved PFC in [10] for Band-A. However, there are no fundamental studies despite reported EMI noise issues to estimate the EMI level for interleaved boost PFC based on the phase shift's dependency, which can be investigated to minimize the DM EMI noise.