esa-sceva/satcom-chunk-collection huggingface dataset:
# Efficient Opportunistic Routing Protocol for Sensor Network in Emergency Applications
## 6 Conclusions  
This paper presents a dynamic, energy efficient opportunistic density cluster-based routing protocol (ODCR) that opportunistically transmits data among sensors and other wireless nodes in disaster and emergency situations. In this ODCR protocol, each node joins in a density cluster-based sensor network and exchanges information with other nodes of the cluster, or each node forwards data opportunistically whenever it encounters another node with a higher probability of data delivery to the destination. We evaluated the performance of the proposed ODCR routing protocol in terms of network energy consumption, packet loss, throughput and packet delivery ratio compared with existing well-known LEACH, TEEN and LORA protocols. Experimental results found that the performance of the proposed ODCR routing protocol is much better than that of LEACH, TEEN and LORA protocols in terms of the above described performance metrics. However, we plan to verify the performance of the ODCR protocol in terms of latency, localization error and other performance metrics in the future. We also plan to include a reinforcement learning-based approach (i.e., machine learning and artificial intelligence [27; 28]) in the MAC protocol and scheduling mechanism to achieve sensor energy efficiency as part of a future work.  
The work presented in this paper is based on the concept provided by [PERSON]-k. Who also contributed to system model, methodology, implementation, validation, writing the paper. Conceptualization and methodology, paper drafting have been done by [PERSON] work as a project coordinator, reviewer, proof-reader of this paper. All authors have read and agreed to the published version of the manuscript.  
This research received no external funding.  
The authors declare no conflict of interest.
# The Prediction Performance Analysis of the Lasso Model with Convex Non-Convex Sparse Regularization
## 3 Lasso with CNC Sparse Regularization
### Convex Condition  
In this subsection, we explore the adjustment of GMC regularization to preserve the overall convexity of the Lasso model (14).  
**Theorem 2**.: _Let \(y\in\mathbb{R}^{n}\), \(X\in\mathbb{R}^{n\times p}\), and \(\lambda>0\). Define the objection function of (14) as_  
\[F^{GMC}_{B}(\beta)=\frac{1}{2n}\|y-X\beta\|_{2}^{2}+\lambda\Psi^{GMC}_{B}( \beta), \tag{15}\]  
_then \(F^{GMC}_{B}(\beta)\) is convex if \(B^{\top}B\preceq\frac{1}{n\lambda}X^{\top}X\) and is strictly convex if \(B^{\top}B\prec\frac{1}{n\lambda}X^{\top}X\)._  
The proof of Theorem 2 is provided in Appendix A.2.  
By constructing the matrix parameter \(B\), we can ensure that the convexity conditions mentioned above are maintained. Similar to [23], when \(X\) and \(\lambda\) are specified, a straightforward method to determine the parameter \(B\) is  
\[B=\sqrt{\frac{\omega}{n\lambda}}X,\qquad 0\leq\omega\leq 1. \tag{16}\]  
Then, \(B^{\top}B=\frac{\omega}{n\lambda}X^{\top}X\) which satisfies Theorem 2 when \(\omega\leq 1\). The parameter \(\omega\) controls the non-convexity of the \(\Psi^{GMC}_{B}\). When \(\omega=0\), \(B=0\) and the penalty reduces to the \(\ell_{1}\) norm. When \(\omega=1\), (15) is satisfied with equality, resulting in a'maximally' non-convex penalty.  
According to Theorem 2, we can deduce the following corollary, which is useful in our proof of algorithm convergence.  
**Corollary 1**.: _For all \(\mu\geq\lambda\sigma_{max}\), \(\Psi^{GMC}_{B}(\beta)+\frac{\mu}{2}\|\hat{\beta}\|_{2}^{2}\) is convex, where \(\sigma_{max}\) is the largest eigenvalue of \(B^{\top}B\)._  
By replacing \(\frac{1}{2n}\|y-X\beta\|_{2}^{2}\) with \(\frac{\mu}{2}\|\hat{\beta}\|_{2}^{2}\) in (A14), we can draw Corollary 1 from the proof of the Theorem 2.
## 3 LIG-Based Wearable Systems for Multifunctional and Intelligent HCI
### Intelligent Speech Recognition and Motion Control System  
The LIG, being thin, flexible, and inexpensive, presents benefits when utilized in popular wearable and HCI systems. Based on the excellent electrical, thermal, and mechanical properties of LIG, [PERSON] et al. leveraged its advantages to produce cost-effective yet high-performing HCI systems, and developed an intelligent speech recognition and motion control system [18]. Figure 12 is the functional concept map of this multifunctional and intelligent system.  
The fabrication process is as follows: a LIG-based sound detector was prepared on a 25 \(\upmu\)m PI substrate with the help of a low-power laser machine (1.3 W). The porous structure of LIG is highly sensitive to vibrations caused by sound waves, making it an ideal material for sound detection. Furthermore, because of its good flexibility and electrical properties, LIG maintains good acoustic performance when it is attached to the curved surface of the human body or robot. Due to the principle difference between the LIG-based microphone and the traditional microphone, the research team designed an intelligent speech recognition algorithm based on one-dimensional CNN to efficiently and accurately recognize the language information received by the LIG-based microphone. To train the intelligent algorithm, the research team used the LIG-based microphone to record datasets of 10 numbers (0-9) and 20 commonly used sentences. By recording each word and sentence 50 times by the male and female, the team obtained 1500 speech samples. By using an end-to-end one-dimensional CNN, the important information in speech commands can be inferred. The intelligent algorithm successfully classified the sounds gathered using the LIG microphone with 98% accuracy.  
The whole system consisted of a LIG-based microphone, an analog-digital converter, a signal processing unit, and a one-dimensional CNN. Based on the intelligent algorithm-assisted speech recognition module, the system could accurately analyze the instructions of the human and control the manipulator to take the corresponding actions.  
This speech recognition and motion control system can have important application values in the field of acoustic HCI systems and speech control robots. Additionally, the acoustic component of this HCI system is inexpensive, costing only a few cents, which greatly enhances its prospects.
## 3 Platform for Real-Life Testing of Communication Protocols
### Monitor Messaging
#### 3.3.1 Monitoring Message Content  
As data transmission chains follow a highly regular pattern, the monitoring data can be viewed as a time series, and therefore, each message must include a timestamp. The timestamp is added to the message when it is created. Additionally, two optional fields  
Figure 10: The architecture of the messaging system.  
are included to gather information about the probe, filled in before the message is sent over the transport channel. To ensure that the broker knows which parser to use for each incoming message, the payload type (payload ID) is included in the proto-carrier message. The content of the monitoring message is summarized in Table 1.
## 4 Network Model
### Network Design  
There is insufficient publicly available data to describe a network of today (including all the installed devices, physical and logical links with their capacities and routing). Therefore, it is necessary to design a Static Base Network (SBN) serving as a starting point for the energy evaluation study. The network design process of the SBN determines installation of fibers and routers with LCs. Furthermore, it determines lightpaths comprising logical links together with their routing as well as routing of traffic demands over the logical topology of the SBN.  
The SBN is computed using a MILP formulation (detailed in the Appendix A) for a two-layer network design minimizing Capital Expenditure (CapEx) cost for the maximum traffic \(d_{a,b}\):  
\[d_{a,b}=\max_{t\in T}\{d_{a,b}(t)\}. \tag{8}\]  
We assume that a router \(n\) (out of a set of routers \(N\)) with capacity \(R_{n}\) can be installed at each node of the network at cost \(x_{n}^{\text{ipr}}\). Similarly, the cost of installation of an OXC in the network is \(\kappa^{\text{oxc}}\). Installation of (two) LCs associated with a corresponding lightpath costs \(\kappa^{\text{lp}}\). Eventually, cost of fiber installation \(\kappa_{e}^{t}\) depends on the length of the corresponding physical supply link \(e\in E\).  
The MILP formulation builds upon established network design models (see, e.g., [31; 32]), and extends them with constraints on IP traffic routing along single shortest paths through the network of installed logical links in order to be in line with commonly used routing protocols such as Open Shortest Path First (OSPF). This is realized by using node potentials that keep track of routing path lengths.
# Design of a Baseband Signal for the 406 MHz Satellite Emergency Radio Transmitter Based on STM32
## 4 Experiment and Comparison  
Figure 5 shows the ITU list of MID country code numbers. The BCH-1 is \"00010001101000100010\", which converted to hexadecimal is 0x31a22; the BCH-1 is \"01100110100\", which converted to hexadecimal is 0x66c.  
Figure 6 shows the results of the first BCH error correcting code and the second BCH error correcting code calculated after setting the setup write program in Figure 6 in the STM32 and printed from the serial port.  
Figure 4: The program flowchart of the COSPAS-SARSAT transmitter.  
Figure 3: The signal flow diagram of the real COSPAS-SARSAT transmitter.  
BCH(127, 106, 3), BCH(63, 51, 2)test:  
receive:  
BCH1:0x31a22  
BCH2:0x66c  
It can be seen that the first error-coded BCH check digit calculated by BCH-1 is expressed as 0x31a22 in hexadecimal number, which is consistent with the list of ITU Central country codes; the BCH check digit calculated by the second error-coded BCH is expressed as 0x66c in hexadecimal number, which is consistent with the list of ITU Central country code numbers. Therefore, the BCH check digit can be calculated using this method.  
Figure 7 shows the actual measurement circuit of the 406 MHz EPIRB in this paper. From Figure 7, it can be found that the STM32 microcontroller is the signal pre-processing module; the COSPAS-SARSAT transmitter is the signal processing module which consist of DDS, LNA, RF bandwidth power amplifier and 406 MHz washboard antenna; and the BeiDou GPS dual-mode positioning module is the acquisition module.  
Figure 8 shows the distress message sent by the 406 MHz EPIRB detected by the CLP beacon detector after the coded baseband signal was transmitted in this way. The main information includes: the measured frequency (406.024326 MHz), the country code (403-China), the longitude (30.5\({}^{\circ}\) N), the latitude (114.25\({}^{\circ}\) E) and the MMSI (the ship's marine mobile identification code = 123456) code. The test result shows \"PASS\", which means the CLP beacon detector has received the distress aler  
Figure 5: The ITU list of MID country code numbers.  
Figure 6: The BCH error correcting code calculated by STM32 microcontroller.  
Figure 8: The message decoded by the detector.  
Figure 7: The actual test circuit of the 406 MHz EIPIRB.  
codes and BCH (63, 51) codes, where the BCH (63, 51) codes and the BCH (127, 106) code are completed in 0.215 ms and 0.448 ms, respectively. But in the traditional way, the BCH (63, 51) codes are carried out in 1.544 ms, and the BCH (127, 106) is finished in 10.976 ms. The encoding rate is effectively improved.
## 2 Experiment
### Test Programs  
#### 2.3.1 High-Temperature Acquisition System  
The test heating equipment was a GWX-1100 high-temperature environmental test furnace (produced by FangRui Technology Co., LTD Changchun, Changchun, Jilin Province, China). The furnace has external dimensions of 550 mm \(\times\) 500 mm \(\times\) 600 mm, chamber dimensions of 300 mm \(\times\) 220 mm \(\times\) 350 mm, a maximum heating rate of 800 \({}^{\circ}\)C/h, a thermostatic control accuracy of \(\pm\)2 \({}^{\circ}\)C, a temperature gradient of 3 \({}^{\circ}\)C and an operating power rating of 5 kW. The test temperature control system was the GWX-1100 Human Machine Interface (HMI) operating mode, which consisted of a temperature control system with an HMI. The heating power was adjustable, and the power output was limited at any time using the built-in touchscreen program. As a result, the temperature inside the furnace could be precisely set and maintained. The high-temperature test equipment and temperature control monitoring system are shown in Figure 3.  
\begin{table}
\begin{tabular}{c c c c c c} \hline \hline \multirow{2}{*}{**Group**} & \multirow{2}{*}{**Specimen ID**} & \multirow{2}{*}{**Rebar Diameter**} & \multicolumn{2}{c}{**Fraction of Steel Fiber by**} & \multicolumn{2}{c}{**Temperature Exposure**} & \multirow{2}{*}{**Number**} \\  & & **(mm)** & **Volume (\(V_{J}\))** & **(T)** & **Number** \\  & & **(mm)** & **(\%)** & **(\({}^{\circ}\)C)** & \\ \hline
1 & SF0T20-\(n\) & 14 & 0 & 20 & 2 \\
2 & SF0.5T20-\(n\) & 14 & 0.5 & 20 & 2 \\
3 & SF1T20-\(n\) & 14 & 1 & 20 & 2 \\
4 & SF1.5T20-\(n\) & 14 & 1.5 & 20 & 2 \\
5 & SF0T200-\(n\) & 14 & 0 & 200 & 2 \\
6 & SF0.5T200-\(n\) & 14 & 0.5 & 200 & 2 \\
7 & SF1T200-\(n\) & 14 & 1 & 200 & 2 \\
8 & SF1.5T200-\(n\) & 14 & 1.5 & 200 & 2 \\
9 & SF0T400-\(n\) & 14 & 0 & 400 & 2 \\
10 & SF0.5T400-\(n\) & 14 & 0.5 & 400 & 2 \\
11 & SF1T400-\(n\) & 14 & 1 & 400 & 2 \\
12 & SF1.5T400-\(n\) & 14 & 1.5 & 400 & 2 \\
13 & SF0T600-\(n\) & 14 & 0 & 600 & 2 \\
14 & SF0.5T600-\(n\) & 14 & 0.5 & 600 & 2 \\
15 & SF1T600-\(n\) & 14 & 1 & 600 & 2 \\
16 & SF1.5T600-\(n\) & 14 & 1.5 & 600 & 2 \\ \hline \hline \end{tabular} Note: SF1.5T200-\(n\) denotes that the specimen with the fraction of steel fiber by volume was 1.5% at 200 \({}^{\circ}\)C, \(n\) denotes the number of specimens, \(n=1\), 2.  
\end{table}
Table 4: Specim details.  
Figure 2: Specim size and photograph (mm).  
The temperature of the bond zone between rebar and SFRC was recorded, using a type-K thermocouple connected to an Agilent 34980A data acquisition instrument. The thermocouple was pre-built in the center of the bond zone between rebar and SFRC.
# An Improved CZT Algorithm for High-Precision Frequency Estimation
## 5 Conclusions  
This paper proposes an improved CZT algorithm for high-precision frequency estimation, which can effectively suppress spectrum leakage. By theoretical analysis and derivation, the bias correction factor \(\mu\) is constructed based on the CZT spectrum, and the approximate solution for the bias correction factor \(\mu\) is derived according to the CZT spectrum. The relationship between the bias correction factor and the true frequency is used to make corrections to the frequency estimation. The simulation results show that the proposed algorithm has a lower estimated frequency mean error and lower RMSE than other algorithms and can effectively suppress the fence effect. In contrast to the CZT Candan algorithm, the proposed algorithm utilizes both the amplitude and phase information and shows a better performance. Moreover, the computation complexity of the proposed improved CZT algorithm is only slightly larger than the basic CZT algorithm, but it has a better frequency estimation performance than the basic CZT algorithm. In addition, the test system for the FMCW radar is applied to verify the effectiveness of the proposed algorithm in actual engineering applications.  
Conceptualization, Y.X. and H.Y.; methodology, Y.X. and H.Y.; software, Y.X.; validation, H.X. and W.Z.; formal analysis, Y.X.; investigation, W.Z.; resources, H.X.; data curation, Y.X. and H.X.; writing--original draft preparation, Y.X.; writing--review and editing, H.Y.; visualization, W.Z.; supervision, H.Y.; project administration, W.Z.; funding acquisition, Y.X. and H.Y. All authors have read and agreed to the published version of the manuscript.  
This research was partly funded by the Key Project of the Science and Technology Commission of Shanghai Municipality (Grant Number 20 JC1416504) and partly funded by the Special Projects for Key R&D Tasks in the Autonomous Region (Grant Number 2022B01009).  
Not applicable.  
The data presented in this study are available on request from the authors.  
The authors declare no conflict of interest.  
Figure 6: The error between the frequency estimates and the reference frequency under different distances.
# Silver Nanoparticles-Loaded Exfoliated Graphite and Its Anti-Bacterial Performance
## 2 Materials and Methods
### Antibacterial Activity and Anti-Adhesion Effect of Bacteria  
The antibacterial activity of Ag-EG was studied against the Gram negative bacterial strain _Pseudomonas aeruginosa_ (ATCC 10145) and Gram positive bacterial strain _Staphylococcus aureus_ (ATCC 27217). The bacterial strains were grown in lysogeny broth (LB) at 37 \({}^{\circ}\)C with continuous shaking at 200 rpm for 12 h. Ten mL bacterial cultures were separated by centrifugation (5000 rpm, 4 \({}^{\circ}\)C), the supernatant was discarded, 10 mL PBS was added and shaken up, then the bacterial solution was separated by centrifugation, this step was repeated three times. Finally, a bacterial solution (approx. 10\({}^{9}\) CFU) without LB was obtained. A mixture of nutrient broth and nutrient agar in 1 L distilled water at pH 7.2 as well as the empty Petri plates were autoclaved, the agar medium was then cast into the Petri plates and cooled. Two to three mg Ag-EG were made into round pieces with diameter of 6 mm. 0.2 mL bacterial solution was homogeneously dispersed on solid medium, then the round piece was placed on the solid medium. The inhibition zone images were collected by a digital camera after 24 h incubation at 37 \({}^{\circ}\)C. Each Petri plate had four Ag-EG round pieces to reduce the error.  
The anti-bacterial adhesion effect was also evaluated by the colony-counting method. The round pieces of EG and Ag-EG were sterilized by ultraviolet light, the _P. aeruginosa_ and _S. aureus_ bacterial strains were washed in PBS by the method mentioned above, then round pieces were incubated with washed bacteria for a couple of hours at 37 \({}^{\circ}\)C. The samples were washed by a combination of sonication and severe stirring to remove all loosely attached bacteria, then the round pieces were stamped on the solid medium. The bacterial communities were counted after 24 h incubation at 37 \({}^{\circ}\)C.
## 3 Results and Discussion
Table 6 presents, for comparison purposes, the performance of the photodiodes designed in the current study and other works reported in literature. \begin{table}
\begin{tabular}{c c c c} \hline
**CMOS Technology** & **n+/p-Substrate (fA)** & **p+/n-Well (fA)** & **n-Well/p-Substrate (fA)** \\ \hline
0.18 \(\upmu\)m & 3701 & 1933 & 1653 \\
0.35 \(\upmu\)m & 1840 & 2179 & 675 \\
0.7 \(\upmu\)m & 4164 & 2205 & 802 \\ \hline \end{tabular}
\end{table} 
Table 5: Dark current (fA) measured at 300 K of the n+/p-substrate, p+/n-well and n-well/p-substrate photodiodes simulated for 0.18, 0.35 and 0.7 \(\upmu\)m CMOS technologies. There are few studied reported in the literature on focused technologies (0.18, 0.35 and 0.7 \(\upmu\)m) nor on specifying the photodetector p-n junction structures. Additionally, the results vary substantially among the studies, which further makes the comparison difficult. Overall, the quantum efficiency of a photodiode depends on the type of semiconductor (including the absorption coefficient), the depth of the junction, the width of the depletion layer, the distance between the charge space region and the ohmic contact, the dielectric coatings existing on the material surface, which affect the optical reflectance and the active area of the photodiode [30]. All these factors may cause the differences between the numerical simulations and the experimental characterizations reported in literature. First, it is important to note that the numerical results presented in Figures 8-10 only took into account the p-n junction, without oxide layers on top of the photodiode's active area, while the data reported in the literature (for instance [1]) includes oxides (with a different number of layers according to the technology), which affect the overall reflectance of the microstructure, also affecting its optical efficiency (when no anti-reflection coatings are considered) [31]. When comparing the simulation results with the experimental results reported in literature, it can be observed that, according to Table 6, the simulation of the n+/p-substrate photodiode in the 0.18 \(\upmu\)m technology has the maximum peak of quantum efficiency in the same region (visible, between 500-700 nm) as the other n+/p-substrate photodiodes reported in the literature. The photodiode designed by [PERSON] et al. [29], although not
## 4 Xanthohumol Derivatives
### Cinnamate 4-hydroxylase (C4H)  
C4H can also be termed 4-monooxygenase, where the electrons necessary for catalysis are provided by NADPH cytochrome P450 reductase (CPR), a flavoprotein colocalized with C4H on the exterior surface of the membrane of the endoplasmic reticulum [112]. C4H catalyzes the first oxidative step in the phenylpropanol pathway in higher plants by converting trans-cinnamate to \(\rho\)-coumarate; this is a typical reaction step in the biosynthesis of most phenolic compounds such as flavonoids, coumarins, lignans, and tansnins, among others [113]. Downregulation of C4H in alfalfa (_Medicago sativa_) and Arabidopsis (_Arabidopsis thaliana_) results in a proportional decrease in lignin content [114; 115]. Reduction of C4H activity in tobacco through antisense repression resulted in reduced content and altered subunit composition of lignin [116].  
For the enzyme application, a modified C4H1 was engineered in yeast, and the new enzyme possesses increased stability and water solubility, which suggested a strategy for the production of a soluble enzyme [96] (Table 1). The first crystal structure of the enzyme C4H1 was recently characterized by lignifying tissues of sorghum (_Sorghum bicolor_) [117]. The resulting structural information, coupled with the steady-state kinetic analysis and absorption spectroscopy findings, revealed a significant degree of structural and functional similarity between C4H and other P450 proteins. In addition, a putative allosteric substrate-binding site in the hydrophobic pocket at the enzyme surface existed.
## 3 Results and Discussion
### Effect of the ZLF Aqueous Extract on High-Fat Diet-Induced Lipid Metabolism Disturbance in Mice
#### 3.3.3 The Effect of ZLF on HDL Cholesterol/Total Cholesterol, and Atherogenic Index  
The ratio of atherogenic index and total cholesterol/HDL-cholesterol was calculated in all mice in the experiment (Figure 5). Taking a chronic high-fat diet in mice induced a significant increase in the atherogenic index (\(p<0.001\)) and in the total cholesterol/HDL-cholesterol ratio (\(p<0.001\)) compared to NCG. However, daily administration of the aqueous ZLF extract at 200 and 400 mg/kg doses significantly suppressed the high values caused by the high-fat diet, which has almost returned to the base range. The reduction was significant for 200 and 400 mg/kg (\(p<0.05\) and \(p<0.01\), respectively) for the atherogenic index, and the reduction in total cholesterol/HDL-cholesterol ratio was significant (\(p<0.001\)) at doses 200 and 400 mg/kg body weight compared to HCG mice. Indeed, a lower total cholesterol/HDL-cholesterol ratio helped prevent atherosclerosis as it was directly related to cardiovascular disease [43]. The ZLF extract significantly decreased the total cholesterol/HDL-cholesterol ratio in fat-overloaded mice, confirming that this extract has a beneficial effect on lipid profile regulation and ultimately prevents cardiovascular disease. This is consistent with other work examining the anti-hyperlipidemia effects of plant extracts [34; 35; 44; 45].  
Figure 5: Effect of the aqueous ZLF extract on the ratio of total cholesterol/HDL-cholesterol (**a**) and Atherogenic index (**b**) in mice exposed to HFD. Data are mean \(\pm\) SEM, \(n=6\). \({}^{\#\#}p\leq 0.001\) versus NCG. * \(p<0.05\), ** \(p<0.01\), *** \(p<0.001\) versus HFD group. ns: not significant.