esa-sceva/satcom-chunk-collection huggingface dataset:
# A Portable Non-Motorized Smart IoT Weather Station Platform for Urban Thermal Comfort Studies
## 5 Discussion and Conclusions  
We successfully developed and tested a non-motorized weather station platform with a portable edge device to measure AT, RH, WS, and GT, and a centralized server. The centralized server accepts connections from multiple edge devices, receives the data stream, performs data processing, and stores it. Furthermore, we minimized the cost of the display screen, unlike [47], by developing a real-time data monitoring interface enabling data collection and real-time monitoring on any device, such as a mobile phone, laptop, or tablet with internet access, that was absent in [47, 54]. We achieved higher atmospheric variable accuracy due to the use of appropriate shielding for sensors and adhered to the ISO 7726 (1998) standard and ASHRAE Handbook of Fundamentals for the GT, which were some limitations of [47]. Additionally, neither [54] nor [47] explored communication performance as we did in this paper, under various urban setups. During our tests, we also considered two scenarios in which the device would be used for thermal comfort and UHI studies.  
Even though the GPS sensor correctly identified the routes taken to measure the atmospheric variables, it was found to be inaccurate within the street. This makes it a good fit for thermal comfort or UHI studies at the neighborhood level using the 'on the Move' method, but not for bio-meteorological, human-scale, or nuanced spatial-scale studies that focus on the street's urban properties. However, this is not the case if a 'Stop and Go' method is used, as the interest points within the streets are predefined, thus making it not dependent on the GPS readings. Similarly, the delayed response leaves us with the question of how accurately the measured value can be associated with the appropriate location while performing the 'On the Move' observation.  
Overall, there will be an interruption in the WS values due to the speed of the vehicle [8], the high response time of the sensor and the inaccuracy of the GPS module within the street make the device inadequate for nuanced human-scale thermal comfort/UHI studies or bio-meteorological studies using the 'On the Move' method. On the other hand, it is recommended to wait for 5 min to allow the device to respond to the location change in the'stop-and-go' scenario before conducting the actual measurement.  
Conceptualization, R.S.B., S.H., F.S., R.E.; methodology, R.S.B., S.H.; Edge-device and interface development, S.H.; validation, R.S.B., S.H., F.S.; formal analysis, R.S.B.; investigation, R.S.B.; resources, R.E.; data curation, R.S.B.; writing--original draft preparation, R.S.B.; writing--review and editing, R.S.B., S.H., R.E; visualization, R.S.B.; supervision, F.S., S.H., C.S.T., R.E.; project administration, F.S., R.E.; funding acquisition, R.E. All authors have read and agreed to the published version of the manuscript.  
This research received no external funding.  
**Data Availability Statement:** Dataset available on request from the authors.  
**Conflicts of Interest:** The authors declare no conflicts of interest.
## 5 Applications of Thermal Images to Future Space Missions
### Target Maker Tracking  
Close-up thermal imaging during descent operations of Hayabusa2 was carried out using the TIR. An opportunity arose to release and track a Target Marker (TM) on 25 October 2018 (see Figure 6). A TM is a 10 cm-diameter spherical ball wrapped with a recursive reflection sheet, and it has been proven that the TIR clearly detects the TM falling to and settling on the asteroid surface as a \"cold sphere\". The TM was not clearly detected by optical images at the solar phase angle of \(>2^{\circ}\) without a flashlight, and if the TM was seen, it tended to be dazzling when a flashlight was used. The first sampling of the asteroid surface material was carried out on 22 February 2019, where the TM was detected again by the TIR as a \"cold sphere\" beside a 1 m-sized boulder nearby the landing site. The known size and shape of TM in an image provides a geometric scale. In the case of S-type asteroid, the TM of low albedo and high emissivity (dark ball) should better be detected easily as a \"hot sphere\".
# Investigating the Effect of Screw Size on the Stress Level in MERO Joint for Space Frame Structures
## 3 Results and Discussion
### Comparing the Factor of Safety (FOS)  
The above-mentioned ball joints underwent the axial loads of 4 and 5 tons, while considering the CK45 (1.1191) steel in accordance with standard DIN EN 10083-2:2006 [32] for the MERO ball joint, as well as the effects of the ball joints of three sizes on the level of stress, which had a decreasing trend with increase in diameter. Table 1 represents the effect of ball joint size on the yield stress level.  
Numerical values related to the factor of safety (FOS) can be calculated through the amount of the yield stress presented in Table 1 and the results of the previous simulations. As shown in Figure 17, amounts of FOS under two loading conditions of 4 and 5 tons are compared in three separate diagrams.  
\begin{table}
\begin{tabular}{c c} \hline \hline
**D (mm)** & **Yield Stress-Normalized (MPa)** \\ \hline
16–100 & 305 \\ \hline
100–250 & 275 \\ \hline \hline \end{tabular}
\end{table}
Table 1: Effect of the ball joint size on the yield stress level.  
Figure 16: A comparison among the effects of the ball joint size variations on the load and constant screw size for three sizes of (**a**) M12, (**b**) M16, and (**c**) M20.  
Figure 17: Comparing the effect of changing screw size on the factor of safety of the ball joint on the axis loads of 4 tons and 5 tons for three sizes of (**a**) M12, (**b**) M16, and (**c**) M20.  
As represented in Figure 17a-c the amount of the FOS is enhanced by increasing the diameter of the ball joint under the considered loading conditions and screw sizes. The highest FOS belongs to the ball joint of 132 mm for screw M24 under the axial load of 4 tons. In addition, these figures show that FOS has roughly a linear and reverse relationship with the amount of the applied load. It is noteworthy that M12 screw size is not recommended for the loads more than 4 tons, since as apparent from above figures the corresponding FOS would be very low and almost below 1 in all the cases.
# On Self-Interference Cancellation and Non-Idealities Suppression in Full-Duplex Radio Transceivers
## 2 Proposed System Model and Techniques
### Linearization
However, in the presence of Rx impairments, BER offers quite strange behavior, and up to 20 dB SNR, BER is relatively high, i.e., even below \(10^{-1}\). Comparison between proposed techniques for self-interference cancellation with work previously carried out in the field of FD communication systems is presented in Table 4.  
Figure 16: Receiver performance; BER vs. SNR. Figure 15: Non-linear LNA with negative feedback linearization technique (**a**); and feedforward linearization technique (**b**). \begin{table}
\begin{tabular}{|c|c|c|c|c|c|} \hline  & \multicolumn{2}{c|}{**Techniques**} & \multicolumn{2}{c|}{**Results**} & \\ \hline
**Analog/RF SIC** & **Digital SIC** & **Linearization Techniques (LT)** & **Analog/RF SIC** & **Digital SIC** & **Reference Papers** \\ \hline Auxiliary path & & & & & \\ (consisting of DAC, IQ, PA and RF attenuator) & Gain factor & - & & & \\ \hline  & & & & Residual linear components by 50 dB & \\ \cline{2-6} Robust algorithm & & & 60 dB & Non-linear components by 20 dB. & [74] \\ \cline{2-6} known as SINC & LS algorithm & - & & 20 dB. & \\  interpolation & & & & Hybrid model enables SI & \\ \cline{2-6}  & & & cancellation near to receiver noise & \\ \cline{2-6}  & & & floor up to 110 dB & \\ \hline One tap filter depicting & & & & Linear Model: 25 dB & \\ \cline{2-6} the delay, phase and & LS estimator & - & 30 dB \& 20 dB & Widely Linear Model: 35 or 50 dB \\ \hline  & & & & Passive isolation: 60–70 dB & - & \\ \cline{2-6} Passive isolation & & & & 60–70 dB & \\ (special antenna  design) & - & & & 100 dB of overall self-interference suppression & \\ \hline  & & & & 100 MHz waveform & \\ \cline{2-6}  & & & & bandwidth: 41 dB total cancellation & - & \\ \cline{2-6}  & & & 20 MHz carrier & \\ \cline{2-6}  & & & bandwidth: 60 dB total cancellation & & \\ \hline  & & & & More than & \\ \cline{2-6}  & & & 40 dB of active & \\  Digitally controlled RF & & & & RF cancellation & \\ \cline{2-6}  & & & gain up to & \\ \cline{2-6}  & & & 80 MHz & \\ \cline{2-6}  & & & instantaneous waveform & \\ \cline{2-6}  & & & & bandwidths & \\ \hline Used a shared antenna & & & & & \\ \cline{2-6}   and a circulator, an & & & & \\ \cline{2-6}   adjustable impedance & & & & \\ \cline{2-6}   mismatch terminal & & & & \\ \cline{2-6}  (IMT) circuit at the & & & & \\ \cline{2-6}   antenna interface is & & & & \\ \cline{2-6}   added for cancellation & & & & \\ \cline{2-6}   of SI & & & & \\ \hline Block-adaptive & & & & \\ \cline{2-6}   Learning algorithm & - & & 54 dB & - & [79] \\ \cline{2-6}   through decorrelation & & & & & \\ \cline{2-6}   for RF cancellation & & & & \\ \hline \end{tabular}
\end{table} 
Table 4: Comparison of proposed work with previous works.
## 4 Discussion
### Future Research  
Beyond addressing the limitations of the current approach, DSPEB opens many directions that could be explored further. We believe that single-date estimation and a global model which combines wave and color information are important directions for future work.  
The results presented in this work show the improvement of accuracy when integrating estimations from multiple dates to create a composite estimate, compared to using the original single-dates estimates. However, a model capable of obtaining single-date estimates with accuracy similar to the composite estimates would be preferable. As mentioned in Section 3.2, an interesting path for future work would be to design the training scheme to maximize single-date accuracy specifically (through e.g., training batch management). We also believe that study of the estimation variability between dates for wave kinematics-based methods such as W-DSPEB and S2 Shores can lead to improvements for single-date SDB estimation.  
A potential direction for SDB is to combine wave and color information to achieve local estimates with high accuracy and global applicability. In Appendix E, we explore ahybrid model which combines estimates from W-DSPEB and C-DSPEB. While the results from this experiment were inconclusive, with the hybrid model performing worse than W-DSPEB in some cases, we strongly believe that a combined model incorporating both types of methods (color-based and wave kinematics-based methods) is the way forward to unlock and extend the applicability of SDB to a global scale covering all types of coastal waters and coastal depths. While we present H-DSPEB as our first steps in this direction by engineering a hybrid model, other possibilities exist including traditional and/or deep learning-based data assimilation techniques for example [52].  
A fundamental direction for future research in deep learning-based SDB is the development of a singular model which can be applied directly to sites without training. Such a model would require the inclusion of multiple sites in a single training dataset (mixed-site training), which should minimize the model's ability to overfit to any site-specific features, and consequently increase the model's ability to generalize to previously unseen sites. We also expect that it would need to include both wave kinematic information and color information, as proposed above. In this work, we demonstrate first steps in this direction with local site training of deep learning models using wave kinematics and color information, showing that deep learning can outperform existing physical methods for coastal bathymetry estimation.
## 3 Implementation of Vehicular VLC System
### Integration of the Proposed Vehicular VLC System to Actual Vehicles  
Figure 5 illustrates the potential integration of the proposed vehicular VLC system with a vehicle's LED tail-light. We utilize a single precision timer, the Ne555, which is commonly employed in existing LED tail-light and headlight lamps. The Ne555 timer operates in monostable, astable, and bistable modes. For our communication application, the bistable mode is used. In this mode, the trigger and (inverted) reset terminals are essential. When the trigger terminal voltage drops below 1/3 Vcc, the output switches to a high state. Similarly, a low signal at the (inverted) reset terminal sets the output to low, as both terminals are unresponsive to high signals. As depicted in Figure 5, an AND gate is placed before the trigger and (inverted) reset terminals, enabling the system to receive binary 1 and 0 from the TX. These signals send a low voltage to the trigger and reset terminals, controlling the tail-light lamp based on the output state. Additionally, a  
capacitor is connected to the control terminal to stabilize the circuit. The threshold and discharge terminals are essential to the system's operation outside the communication circuit. According to Texas Instruments, the Ne555's output pulse rise and fall times are 100 ns, ensuring sufficient data exchange for the proposed vehicular VLC system.
## 2 Muons  
### Properties of the Muon and Muon Capture  
Muons are elementary particles (leptons) identified by the Greek letter \"\(\mu\)\" that can be positively or negatively charged. With a mass that is almost 207 times the mass of the electron, a negative muon is considered a \"heavy electron\", with an electric charge of \(-1\) and \(\
icefrac{{1}}{{2}}\) spin. As an unstable particle, the muon has a mean lifetime of 2.2 \(\mu\)s. The negative muon, other than the decay process, can experience capture by an atom, giving rise to the so-called \"muonic atom\" (Figure 1): the time scale of this process is in the order of \(10^{-13}\) s.  
Muonic capture starts in the outer shells of an atom, around \(n\) = 14, and the first low energy transitions interact with the outer electrons giving a strong Auger effect. As \(n\) decreases, generally from \(n\) = 5, radiative transitions become dominant, with the emission of high energy X-rays. As the muon arrives at the 1 s level, it can either decay or be captured by the nuclei of the atom. If the atomic nuclei is heavier than magnesium, capture by the nuclei is more likely to occur: the nucleus goes to an excited state that can lead to the emission of one or more neutrons and gamma rays. For a complete survey of muon capture and general applications, we recommend [9; 10; 11].  
Figure 1: Muonic capture process. The muon then has a finite probability of being captured by the nucleus and may emit a gamma. The figure was taken and adapted with permission from Ref. [7] © 2016, Elsevier Ltd.  
Given the bigger mass of the muon compared to that of the electron, muonic X-rays are highly energetic (from 0.01 MeV to 6 MeV), even for low Z materials (Figure 2). In most cases, the probability of the muon's atomic capture is estimated to be proportional to the total number of electrons, as reported in Fermi and Teller [12] (although, some detailed models have been developed to account for some inconsistencies [13; 14; 15]). The detection of these high energy X-rays (and gamma) emitted from the muonic atom is the basis of the technique. Since the radiations are characteristic of the emitting atom (Figure 3), muonic atom X-ray spectroscopy is a very effective probe for non-destructive elemental characterization.  
Figure 3: _Cont._  
Figure 2: K-alpha energy values for the elements of the periodic table. Values are listed in [8; 12]. Data was taken and adapted with permission from Ref. [7] © 2016, Elsevier Ltd.
# Practical Work of Three-Phased Induction Motor Modeling in a Classical Spreadsheet Software
## 3 Equivalent Model of the Induction Motor
### Equivalent Model at No-Load: \(s=0\)  
To identify the equivalent model of an induction motor at no-load, the three-phase asynchronous motor is powered by a three-phase network, and its rotor is attached to a direct current (DC) motor supplied with an adjustable voltage. The power supply of this  
Figure 5: The electrical scheme and its equivalent Fresnel diagram when the slip \(s=0\).  
Figure 6: Equivalent scheme of one phase of the motor.  
DC motor is intended to drive the rotor in the direction imposed by the network and reach the synchronism speed \(\Omega_{S}\) (with a slip \(s=0\)).  
At this operating point, we note \(V_{0}\), which is the root mean square (RMS) value of a simple voltage; \(I_{0}\) is the RMS intensity of a line current; \(P_{0}\) is the power supplied by the network; and \(\cos\varphi_{0}\) is the power factor at synchronism. In this operation, the emf (electromotive force) induced in the rotor is zero, as well as the intensities of the rotor currents and the electromagnetic torque. The absorbed power \(P_{0}\) only compensates the losses in the stator. Since Joule effect losses at no load can be neglected, thus saving a great deal of calculations, iron losses \(P_{IS}\) can be written as  
\[P_{IS}\approx P_{0}=3\cdot V_{0}\cdot I_{0}\cdot\cos\varphi_{0}. \tag{5}\]  
For each phase of the three-phase power line, we accounted for this situation with an equivalent model, as illustrated in Figure 5, where the motor is similar to a dipole associating, in parallel, a resistance \(R_{I}\) and a reactance \(X_{m}\). This dipole, supplied with the simple voltage \(v_{\beta}\), must absorb a power equal to \(\frac{P_{0}}{3}\) with a power factor \(\cos\varphi_{0}\). The intensity of the absorbed current in this situation has the RMS value \(i_{0}\). The value of \(R_{I}\) highly depends on the supply voltage frequency.  
The equivalent model at synchronism of an induction motor accounts for the intensity \(i_{O}\) and for the active power \(P_{0}\approx P_{IS}\). In addition, the reactive power \(Q_{0}\) accounts for the magnetizing inductance of the motor, which is modeled with the inductance \(X_{m}\).  
The first two values of the equivalent scheme, \(R_{I}\) and \(X_{m}\), can be found thanks to the following formulas:  
\[R_{I}=\frac{3\cdot V^{2}}{P_{0}}, \tag{6}\]  
\[X_{m}=\frac{3\cdot V^{2}}{Q_{0}}. \tag{7}\]  
In addition, the phase shift angle \(\varphi_{0}\), which is visible in Figure 5, can easily be calculated using the following formula:  
\[\tan\varphi_{0}=\frac{R_{I}}{X_{m}}=\frac{Q_{0}}{P_{0}}. \tag{8}\]
# FirepanIF: High Performance Host-Side Flash Cache Warm-Up Method in Cloud Computing
## 3 Design
### Cachemior  
Our previous work devised Cachemior (_Cache migrator_) to enable a hot start of the host-side flash cache [15]. As depicted in Figure 2, Cachemior consists of the following three components in each host server: hot cache monitor, hot cache messenger, and cache warmer.  
The hot cache monitor is implemented in the flash cache management system (i.e., EnhancedO) and analyzes the host-side flash cache in the host machine. It identifies which cache block is frequently used or less recently used. It maintains a sorted list (i.e., the hot cache list in Figure 2) where frequently accessed cache blocks are placed toward the head of the list. Each cache block is associated with the logical block address of the shared storage server. As the list only includes the logical block addresses, the list size is relatively small compared to the cache size. For example, when the size of the host-side flash cache is 20 GB, the maximum size of the hot cache list is under 20 MB.  
The hot cache messenger is in charge of transmission of the hot cache list between host servers. The messenger in the source node sends the sorted list to the destination node when the migration occurs, and the messenger in the destination node receives it. After receiving the list, the cache warmer in the destination node reconstructs or warms up the host-side flash cache by accessing the shared storage server in the background with a separate thread. As the cache warmer iterates the list from the head, frequently accessed blocks are restored earlier in time than the less recently used ones. If a target item in the list is already placed in the cache by the activity of the migrated VM, the corresponding block does not need to be accessed again. We call this procedure as preloading because the data will be loaded into the flash cache before they are accessed by the VM.  
_Limitations_: After VM migration, Cachemior starts to warm up the host-side flash cache in the destination node. The separate thread in the cache warmer continuously copies cache items from the shared storage server using the hot cache list. However, simultaneously, the VM starts to access the shared storage server for executing its I/O-intensive workloads, and this situation may cause storage and network congestion on the shared storage server. As a result, the host-side flash cache would warm up slowly, and the performance of the I/O workloads on the VM may also deteriorate.
## 3 Optical Coupling between the III-V Device Layer and the Silicon Waveguide Layer
### Grating Coupler Interfaces  
For the integration of surface illuminated III-V photodetectors on silicon PICs, a vertical grating coupler interface can be used [11; 12; 13; 14; 15]. Figure 4a schematically shows this coupling scheme where the light confined in a silicon waveguide is diffracted vertically to the III-V photodetector bonded on the grating coupler. The required photodetector length depends on the grating coupler strength. An important design consideration in this coupling structure is to maximize the directionality of the grating (the ratio of optical power diffracted upwards to the total diffracted power). A vertical cavity is formed by the reflection at the DVS-BCB/III-V interface at the top and the SiO\({}_{2}\)/Si substrate interface at the bottom. This means that the directionality depends on the exact location of the SOI grating in this cavity. By optimizing the DVS-BCB bonding thickness and buried oxide thickness, the directionality can be optimized. Figure 4b shows a two-dimensional full vectorial simulation of the absorbed power in a bonded III-V photodetector as a function of the DVS-BCB thickness (design A). Adding an anti-reflection coating between III-V material and DVS-BCB avoids the formation of such a vertical cavity, resulting in a much more robust optical coupling (design B).