## 5 Simulations and Experimental  
The control strategy of the predictive current is simulated in MATLAB(R2013), containing the code of the control algorithm, as shown in Figure 8. When experimentally implementing predictive control, the same procedure was rewritten in the C language and the alpha and beta currents were calculated. In the MATLAB/SIMULINK environment, the load current prediction (Equation (14)) and back EMF estimation (Equation (17)) are considered. The system parameters \(V_{dc}=800\,V\), \(L=10\,\mathrm{mH}\), \(R=0.02\,\Omega\), and \(e=311V_{peak}\) have been taken into account for the simulations. The current and voltage in one of the phases of the load are simulated for a sampling time \(T_{s}=10\,\mathrm{\SIUnitSymbolMicro s}\). There is no steady state error from the current, but there is an obvious ripple. The ripple is significantly reduced when the smaller sampling time \(T_{s}=3\,\mathrm{\SIUnitSymbolMicro s}\) is adopted. However, by reducing the sampling time, the switching frequency increases, as shown in the load voltage comparison shown in Figure 13. The inverter output phase voltage is shown in Figure 11. When the reference voltage value rises from 500 V to 800 V, the change of the capacitance voltage is shown in Figure 12.  
Figure 11: Output voltage of phase A.  
Figure 10: The cost function flow chart of the T-type inverter model prediction control algorithm. As shown in Figure 13, the value of the reference power is changed at \(t=0.05\,\mathrm{s}\), and the corresponding reference current phase can still stably track the grid voltage phase, and the response speed is fast. With the change of the reference current, the voltage of the divider capacitor becomes more and more stable when the weight factor increases, and the two are close to equal, as shown in Figure 14.  
When changing the value of the reference power, the system can respond quickly. As shown in Figure 15.  
Figure 14: Capacitor voltage of \(C1\) and \(C2\). Figure 12: Change in the reference voltage value. Figure 13.0 The voltage phase and current phase are consistent. At the same time, the control level of the voltage-dividing capacitance increases with the increase of the weighting factor when observing the increase of the magnitude of the weight factor of the division of the voltage-dividing capacitance, which is the same as the conclusion, as shown in Figure 13.1  
As shown in Figure 17, it is obvious to say that the rise of the weighting factor of the current tracking can optimize the THD from 0.15% to 0.10%. Figure 13.2 The influence of adjusting the weight factor of the capacitor voltage. Figure 13.3 The influence of adjusting the weight factor of the capacitor voltage. Figure 13.4 Power tracking. The proposed control method requires a higher sampling or data acquisition frequency. Given the new technologies available for DSP, the foregoing fact should not be a problem. It is worth mentioning that the sampling time is always a fixed position in the sampling period, to facilitate the acquisition of measurement data and to avoid the problem of the switching the power devices. The algorithm is implemented on a Texas Instruments DSP using the same sampling frequency. The algorithm was implemented on the Texas Instruments TMS320F2812 DSP using the same sampling frequency, and similar results in processing time were achieved. The experimental platform is shown in Figure 18 to determine whether the driving circuit can work normally, which plays a key role in the whole system's working state. First, according to the working principle of the driving circuit analyzed above, we designed and built the corresponding driving module. The drive signal is shown in Figure 13.5  
The waveforms in the same bridge arm are supposed to be complementary to each other.