Abstract:
A system that varies the brilliance of light bulbs in accordance with modulated audio signals. The audio signals are first compressed and then passed through a comparator. The comparator has two inputs, one of which is the aforesaid compressed audio signals. The other input is a control input which receives a second voltage in the form of a series of impulses. The compressed audio signals pass through the comparator if and when their voltage is higher than that of said second voltage.

Description:
RELATED APPLICATION 
     We claim the benefit of our prior provision application Ser. No. 60/846,964 filed Sep. 25, 2006, entitled TIMBRE LIGHTING CONTROLS 
    
    
     BACKGROUND OF THE INVENTION 
     It is well known to provide an electrical system for producing varying light beams in accordance with music or other audio input. Such systems have converted the music or other audio into electrical signals which are fed into a high frequency filter, an intermediate frequency filer and a low frequency filter. The output of each filter feeds a service such as a light emitting diode or incandescent bulb. See, for example, the following United States patents: 
     
       
         
               
               
               
               
             
           
               
                   
                   
               
               
                   
                 U.S. Pat. No. 
                 Inventor 
                 Date 
               
               
                   
                   
               
             
             
               
                   
                 1,977,997 
                 Wallor 
                 October 1934 
               
               
                   
                 3,228,278 
                 Wortman 
                 December 1966 
               
               
                   
                 3,720,939 
                 Polenak 
                 March 1973 
               
               
                   
                 4,771,280 
                 Molinaro 
                 September 1988 
               
               
                   
                 5,501,131 
                 Hata 
                 March 1988 
               
               
                   
                 3,815,128 
                 McClure 
                 April 1974 
               
               
                   
                 3,111,057 
                 Cramer 
                 October 1959 
               
               
                   
                   
               
             
          
         
       
     
     Previous implementations of prior art light control have a very poor response to the audio signal, because of the drastically non-linear designs within the prior art of SCR and Triac firing circuits. This problem causes a very poor response of the output voltage to changes in the audio. U.S. Pat. No. 3,815,128 demonstrates the typical problem of drastic non-linearity of the output voltage response to the audio signal. This is shown by circuit analysis and circuit simulation (SPICE) of the above mentioned patent. The combination of these two problems of compression and non-linear firing circuits produce very poor light response to music. 
     Another critical feature that the prior art that has overlooked is the importance of the proper use of compression. The lack of proper compression results in brings about a shortcoming of responsive, consistent results. This is typical of the prior art. 
     SUMMARY OF THE INVENTION 
     The present invention is an apparatus and method for changing light source intensity according to sound variations that cause light sources to respond in unparalleled synchronization to every subtle nuance of harmonics. 
     The apparatus and method that produces AC output voltages to drive light sources wherein the AC output voltages to drive the light sources are directly proportional to a source of audio voltage, such as music, with minimum deviation from a linear relationship between the amplitude of the audio and the amplitude of the AC output voltage(s) to drive the source(s) of light. 
     The comparator circuit function is unique by virtue of the inputs used to produce the relationship between the tailored audio signal(s) and the output AC pulse(s); obtained by the input(s) used, the reference waveform “ramp signal(s)” and the other signal input(s) derived from the audio signal(s). 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         FIG. 1  is a block diagram of the preferred form of the invention. 
         FIG. 2  is a block diagram of the detector circuit  150  for the preferred form of the invention. 
         FIG. 3  is a block diagram of the detector circuit  150  for embodiment 2 of the invention. 
         FIG. 4  is a block diagram of the detector circuit  150  for embodiment 3 of the invention. 
         FIG. 5  is a block diagram of the revised band filters  60 ,  70 , and  80 , which used operational amplifiers to comprise active filters to switched capacitor filters for embodiment 2. This diagram shows the use of a clock to set the frequency of the filters. 
         FIG. 6  is a block diagram of item  40 . 
         FIG. 6A  is a functional block diagram and typical voice application of Analog Devices SSM 2265. 
         FIG. 7  is a block diagram of item  40  as changed for embodiment 2 
         FIG. 8  is a block diagram of item  40  as changed for embodiment 3. 
         FIG. 9  is a block diagram of added items for embodiment 3. 
         FIG. 10  is a block diagram of the power supply  250  as used in the preferred embodiment. 
         FIG. 11  is a block diagram of output drive for embodiment 5 for driving RGB LED&#39;s. 
         FIG. 12  is a detailed schematic of the ramp generator as used in the preferred embodiment. 
         FIG. 12A  is a graph of the ramp generator wave forms. 
         FIG. 12B  is a block diagram of the preferred form showing the inputs to and output from the comparator. 
         FIG. 12C  is the same as  12 A, but at a different voltage. 
         FIG. 13  is block diagram of embodiment 4 and the output drive for the use of pulse width modulation. 
         FIG. 13A  is a block diagram Embodiment 4. 
         FIG. 14  is a detailed schematic of items  370 ,  380 , &amp;  390 , of  FIG. 11 , RGB drive. 
         FIG. 15  is a detailed schematic of the output RGB drives  400  through  480  of  FIG. 11 . 
         FIG. 16 , Embodiment 6 is a block diagram of a change for use in an auto or RV from a 12 volt battery. 
         FIG. 17  is a block diagram of embodiment 7 which is used to provide a drive signal such as a modulation signal for lasers. This embodiment does not use the comparators, and output drive, however, this embodiment may be added to any of the previous embodiments. 
     
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     Item  250  is the power supply for the electronics in the unit (See block diagram,  FIG. 10 .). It supplies a regulated 8 volts dc, a regulated 5 volts dc and 4 volts dc plus a sync signal  260 . The 8 volts dc is the positive voltage for the amplifiers  50 ,  90 ,  100 , and  110 , and the band filters  60 ,  70 , and  80 , and the comparators  310 ,  320 , and  330 . The regulated 5 volts dc is the supply voltage for the preamp  40 . The 4 volts dc is the reference voltage for the amplifiers  50 ,  90 ,  100  and  110 , and the band filters,  60 ,  70 , and  80 . The 4 volts is the zero output level of the amplifiers  50 ,  90 ,  100 , and  110 , and band filters  50 ,  70 , and  120 . The sync signal  260  for the ramp generator  180  is developed in the power supply at the zero crossing of the ac line voltage. This power supply differs from the usual by the addition of diode  353  between the bridge rectifier and the filter capacitor  355 , and the addition of resistor  352 . There is at the junction of bridge rectifier  351 , resistor  352  and diode  353  a half wave, unfiltered signal that drops to zero each time the ac line voltage crosses zero. This provides a sync signal to synchronize the ramp generator with the line voltage. 
     Item  20  is a source of music from an external source. This may be from a microphone or microphones, audio output from a CD player, computer, radio or etc. 
     Item  30  is a means to select between an external source and the internal microphone. Two input jacks have power provided for two electret type external microphones through two resistors such that these same two jacks provide for input from other sources such the audio output from a CD player, computer or etc. A jack for a high impedance microphone maybe provided, this jack has a built in switch that transfers the input from the internal microphone to this input 
     Item  120  may have an internal electret type microphone. 
     The input signal from item  30  feeds a special integrated circuit amplifier, an Analog Devices (Analog Devices, One Technology Way, P.O. Box 9106, Norwood, Mass. 02062-9106) SSM2165-1 (See  FIG. 6A ), which has AGC (automatic gain control), compression and a noise floor. 
     Analog Devices SSM2165-1 Component 
     See FIG.  6 A 
     
       
         
               
               
               
             
           
               
                   
                   
               
               
                   
                 Type 
                 Value 
               
               
                   
                   
               
             
             
               
                   
                 C1 
                 0.1 μF 
               
               
                   
                 C2 
                 0.1 μF 
               
               
                   
                 C3 
                  22 μF 
               
               
                   
                 R1 
                 500 ohms 
               
               
                   
                 R2 
                 500 ohms 
               
               
                   
                 R3 
                 25K 
               
               
                   
                   
               
             
          
         
       
     
     This amplifier has provisions for setting the compression ratio, and the AGC time constant. The compression ratio is set with a resistor at about 5:1, and the AGC time constant is set with a capacitor at about 100 milliseconds. Signals below the noise floor of about 500 microvolts are rejected and not amplified.  FIG. 6  is a block diagram of item  40 . Capacitor  42  bypasses high frequency noise to ground. Capacitor  41  passes the audio signal to the special amplifier  43  (Analog Devices SM2265-1) while blocking dc., capacitor  44  couples the signals from the input amplifier of amplifier  43  to the VCA (Voltage Controlled Amplifier) section of amplifier  43 . Capacitor  45  adjusts the AGC response time of amplifier  43 . Resistor  46  adjusts the compression ratio of amplifier  43 . For example, such ratio may be approximately 5:1. The output from amplifier  43  is coupled through capacitor  47  to the following amplifier item  50 . 
     The dynamic level of music can vary of a wide range; because of this so therefore there is a clear-cut need for accurately controlled compression. A CD or radio playing music will vary for most songs from about 15 to 20 dB. This is a logarithmic scale; a 15 dB change is a variation of sound intensity of a 32:1 change; a 20 dB change is a change of 100:1. Some music may have an even wider dynamic range such as a live band or orchestra. A 20 dB corresponds to an approximate change from soft, at approximately 60 dB, to loud at approximately 120 dB. Very loud would be approximately 100 dB. 
     A 15 dB change picked up by a microphone would produce a variation in the voltage from the microphone of 32 times; for example a change from 0.63 volts to 2 volts; if this were amplified 2.5 times the signal would be 0.158 volts to 5 volts. 
     This 32 times variation can not be well reproduced by the intensity of the light. A desirable variation in the lights that would be pleasing would be about 8:1 to 10:1. This would give a variation from dim to bright that would be acceptable. If an 8:1 variation were desirable for a 20 dB change in the music then a compression ratio of 32 divided by 8 would give a needed compression of 4. A compression ration of approximately 5:1 was selected for the preferred form because it gives a pleasing response to music; for a 20 dB change in music this gives a variation in light intensity of about 6:1. 
     The preferred form makes use of an integrated circuit amplifier from Analog Devices SSM2165 that was designed for use in data transmission system and for intercoms that provides both compression and AGC operation. The compression ratio in the preferred form, is set to approximately 5:1; thus, a change of 10 dB (a ten times variation in the sound level) results in a signal voltage change of 2:1 instead to a 10:1 change—thus the light power output will vary by 2:1 instead of on and off. 
     With the lack of compression there would be produced an on-off blinking of the lights in response to the variation in loudness of the music. Use of AGC (automatic gain control) is used to adjust the signal within range for slow changes; such as a change from a loud passage to a soft passage, but this can not compensate for faster changes in the volume of tones (The AGC time must be set slower than the lowest tone frequency, usually 2 to 5 times the time for the lowest tone—for music which has base tones down to 20 Hz, this would require the AGC response be no faster than 100 milliseconds to 250 milliseconds.) The combination of the having a linear output drive, and compression set at about 5:1 gives a very good response of the lights to music being played; such that subtle variations in the volume of music such as vibrato which shows up in the response of the lights. 
     The input to amplifier  50  is from the output pre-amp  40 . The gain control of this amplifier  50  is available on the front panel as an operator control; this controls the signal level to the following active filters  60 ,  70  and  80 . This gain control sets the overall brightness of the lights connected to the outputs of item  220   
     A three band active filter  60 ,  70 , and  80 , separates the audio signal into three channels, a low frequency signal channel, a mid frequency signal channel, and a high frequency channel. This filter is comprised of integrated circuit amplifiers connected to form a three band active filter. The outputs of the filters  60 ,  70  &amp;  80  are passed to amplifiers  90 ,  100  and  110 , respectively. 
     Item  90 ,  100 , and  110  are amplifiers, one for each band. The high band amplifier  90  and the low band amplifier  110  have operator controls to set the gain of these amplifiers. Amplifier  100 , the midrange amplifier, has fixed gain. The gain of the midrange is set by the adjustment of the gain of amplifier  50 , the brightness control. The relative brightness of the high and low bands in relation to the midrange band is set by the gain controls of the high band amplifier  90 , and low band amplifier  110 . 
     Item  130 ,  FIG. 1  is a potentiometer arranged to provide a dc voltage in lieu of the output of the amplifiers  90 ,  100  and  110 . This provides a means of switching the operation of the lighting controls from the response to music to a constant light level set by the dimmer control item  130 . 
     Item  140  is a means of switching from response to music to dimmer control of all three channels from either dimmer control or response to the audio signal. This is selected by the operator with a switch. Item  140  switches the input to the detectors from amplifiers  90 ,  100 , and  110  to the output of the dimmer control  130 . 
     Item  150 ,  160  &amp;  170  are detectors that convert the audio signals to pulsating dc voltages (see  FIG. 2 ). This consists of a diode  151 , resistor  152 , and capacitor  153  circuit except for the high band  170  which uses a transistor as item  151  instead of a diode to reduce the charge time of the capacitors at the higher frequencies. Resistor  152  provides for the discharge of the capacitor in the detector circuit. These detectors  150 ,  160 , and  170  detect and convert only the positive going portion of the audio signals to give only one half wave detection (½ wave rectification.). There is provision, with soft select switch  155  for switching in added capacitor  154  to increase the discharge time of the detector. Adding in this capacitance gives the lights being driven a “softer” appearance in response to music. This soft select switch  155  is a FET (Field Effect Transistor) which is turned on to add in the capacitor in response to the select signal from item  280 . This softer appearance of the lights is due to this added capacitance slowing the response of the lights to the changes in the amplitude of the audio signal. For use with LED&#39;s it is desirable to have a slower or longer response than when used with incandescent lights; this is because incandescent lights have a heating and cooling time when they change intensity whereas led lights do not have this heating and cooling time but have an instant response to changes. 
     Item  280  is an operator controlled switch to select the sharp or soft response of the lamps connected to outputs  220 , by switching in the added capacitance in the detectors  150 ,  160 , and  170 . 
     Items  180 ,  190 ,  200 ,  210 ,  310 ,  320 , and  330  comprise three linear firing circuits, that is, these circuits provide an approximately linear change in the output voltage versus the change in voltage from the detector circuits  150 ,  160 , and  170 . It is desirable to use a linear firing circuit so that the brightness of the lights will vary in directly in proportion to the variation of the compressed audio signal; this presents a good visual response of the lights to the changes in loudness of the music in each band. This also results in the lights  230  shown a response to changes in music volume such as vibrato to give a very pleasing response. Item  180  (See  FIGS. 12 &amp; 12A ) produces a near linear ramp with its high point at the end of the zero crossing of the ac line voltage and decays to its low point at an approximately linear rate at the start of the next zero crossing of the ac line voltage. Transistor  180   e  is turned on through diode  180   a  and zener diode  180   b  when the voltage of the sync signal  260  from the power supply  250  drops low at each ac line zero crossing. When transistor  180   e  is turned on the voltage at the junction of transistor  180   e  collector, capacitor  180   f , transistor  160   g  emitter, and resistor  180   j  is pulled upward reducing the voltage across capacitor  180   f  by discharging it through resistor  180   d . This is the high point of the ramp. This high voltage point of the ramp is clamped by transistor  180   g  to approximately 5.7 volts. Resistor  180   h  limits the base current through transistor  180   g  while it is clamping the ramp voltage. At the end of the zero crossing sync signal  260  from the power supply, transistor  180   e  is turned off and the capacitor  180   f  discharges through resistor  180   j  and potentiometer  180   k  until the next zero crossing sync signal  260  occurs. Resistor  180   c  provides a quick discharge path of the junction capacitance of diode  180   a , zener diode  180   b , and the emitter base of  180   e  so that transistor  180   e  is quickly turned off at the end of each zero crossing sync signal  260 . Potentiometer  180   k  is for adjustment of the low point of the ramp voltage at the end of each one half cycle of the ac line voltage, this low point occurs at the start of the next sync signal  260 . This low voltage point of the ramp signal is set just above the zero voltage output (no audio signal) of the detectors  150 ,  160 , and  170  by potentiometer  180   k  at approximately 3.7 volts. The adjustment of potentiometer  180   k  is set during manufacturing test. This ramp voltage from the ramp generator  180  is the reference voltage for comparators  310 ,  320 , and  330 . Since the zero output voltage of the amplifiers  90 ,  100 , and  100  is 4.0 volts dc (Set at ½ the 8 volts dc supply voltage from the power supply  250 .) then the zero output voltage from the detectors  150 ,  160 , and  170  is approximately one diode voltage drop lower, and the zero output voltage of detectors  150 ,  160 , and  170  will be approximately 3.5 volts dc. So the low voltage point of the ramp is just above the zero voltage output of the detectors  150 ,  160 , and  170 . 
     Items  190 ,  200  and  210  are output drivers. They have optically coupled triacs which drive power triacs to provide the switching of ac power to the output receptacles  220  to power the lights  230  that are plugged into the output receptacles. The output receptacles are standard ac receptacles into which lights, strings of lights, such as “Christmas lights”, strings of LED&#39;s (Also “Christmas” lights.) may be plugged in. Any lights that operate at 120 volt ac except fluorescent lights or light fixtures with dimmer controls may be used. The comparators  310 ,  320 , and  330  compare the signal from the detectors  150 ,  160 , and  170  to the ramp signal ( FIGS. 12B &amp; 12C ). Consider detector  150  and comparator  310 : When there is no audio signal into detector  150  from amplifier  90  the voltage on the output of detector  150  will be at about 3.5 volts; when this is compared to the ramp at the inputs of comparator  310 , there will be no switching of the output of the comparator  310  to the output driver  210 , and thus no output voltage. As the audio input to the detector  150  from amplifier  90  increases enough to produce 3.8 volts (as an example.) then comparator  310  output will switch when the ramp voltage drops just below the 3.8 volts to produce an output signal to the output drive  210  shortly before the zero crossing. This will switch the output drive  210  on late in the cycle so that the conduction period of the triac in output drive  210  is short, producing only a low voltage output to the light connected to the output. This switching of comparator  310  will occur when the audio signal from detector  150  exceeds the ramp voltage from ramp generator  180 . When the audio signal is further increased, the output of the comparator  310  will occur earlier in the ac cycle turning on the triac in output drive  210  earlier in the ac cycle and thus producing more output voltage to the light that is connected to the corresponding receptacle in  220 . The earlier in the half cycle that the triac in output drive  210  occurs the higher the output voltage will be. Thus there is a near linear relationship between the amplitude of the audio signal from the detector and the output voltage and thus the intensity of the light or lights connected to the output receptacles. With a resistive load the power in the load is; P=V^2/R, where P is the power, V is the voltage, and R is the resistance, and V^2 is the voltage squared. This would seem to indicate the brightness of an incandescent lamp would vary as a function of the voltage squared; however this is not true. The power and brightness of an incandescent lamp is proportional to the voltage; this is true because the resistance of an incandescent light bulb increases with power, from a low value when cold to a much high resistance when hot. Thus there is a near linear variation of voltage from output driver  210  proportional to the amplitude of the audio or music signal and thus there is a near linear variation of brightness of the light to audio signal strength. The voltage from the output drivers  190 ,  200 , and  210  are connected to the output receptacles  220 . LED&#39;s have a linear resistance, that varies with the current through them voltage so they will similarly vary in brightness with voltage Incandescent lights or strings of lights or LED strings designed for operation from 115 or 120 volts ac may be plugged into these output receptacles. Any incandescent or LED light designed to be plugged into the standard ac power outlets may be used, only limited by the power rating that must be within the power rating of the lighting control. This light control can be scaled for low or high power and can be scaled for other line voltages and frequencies as may be used in other countries. 
     Embodiment 2 
     Embodiment 2 differs from the preferred form in the following items: 
     Item  250  is the power supply and is changed in Embodiment 2 to provide a regulated plus 5 volts, a regulated negative 5 volts and the sync pulse for the ramp generator item  180 . 
     Item  43 , an amplifier (See  FIG. 7 ), is changed from Analog Devices SSM2165-1 to Analog Devices SSM2167-1. Resistor  48  and potentiometer  51  provide a means for the operator to adjust the noise floor, which sets the level at which the background is rejected. Resistor  49  and potentiometer  52  provide a means for the operator to adjust the compression ratio and thus the response of the lights connected to the outputs to the lights to be adjusted for the most pleasing response to the music. 
     Items  60 ,  70  and  120  (See  FIG. 5 ) are three band filters. These filters are changed from a three band filter using operational amplifiers to three switched capacitor filters. The band filters in this embodiment are set with a much sharper cutoff between bands. This means there is almost no overlaps of bands. The switched capacitor filters used are integrated circuit switched capacitor filters, Linear Technology LTC1068. The filter characteristics of the switched capacitor filters using the LTC1068 are set by resistors and by the clock frequency. The cutoff at the edge of the bands is set to be much sharper, with much less overlap between bands than in the preferred form. 
     The clock item  271 , a Linear Technology (1630 McCarthy Blvd. Milpitas, Calif. 95035-7417) LTC1799) (these are added into Embodiment 2 see  FIG. 5 ), and provides the clock frequency directly for the high band switched capacitor filter  60 . The clock frequency is divided in half by the divider  272  to provide the clock frequency for the midrange switched capacitor filter  70 . The frequency from divider  272  is again divided in half by divider  273  to provide the clock frequency for low band switched capacitor filter  120 . The frequency of the clock  271  is adjustable by the operator over a 4 to 1 range. When the nominal clock frequency is reduced by one half all three filters  60 ,  70  and  120  are lowered in range by one octave. When the nominal clock frequency is doubled all three of the filters are raised in range by one octave. This provides a means for the operator to change the response of the lights to music to suit instruments or vocalists, as for example if a piccolo is being played or a soprano is singing it would probably be desirable to raise the response of the filters and thus the lights, or if a bassoon or bass were being played it would probably be desirable to lower the response of the filters and thus the lights to give a more pleasing response of the lights. 
     The detectors (See  FIG. 3  Embodiment 2) differ from those in the preferred form. Instead of a simple diode or transistor ½ wave detector as is used in the preferred form a full wave operation amplifier detector is used, item  161 . This is followed by a transistor  162 , to avoid loading the detector, which charges capacitor  164 . Resistor  163  provides the discharge of capacitor  164 . For soft response capacitor  165  is added to increase the discharge time for the detector, circuit. This capacitor  165  is switched in by soft select switch  166  which is a FET transistor, which is turned on by a signal from item  280  response select. It is also possible to use a different clock for each band and thus be able to independently move the bands in frequency. 
     Embodiment 3 
     Item  120 , the internal microphone is not included in Embodiment 3. 
     Item  30  is changed in embodiment 3 by adding provisions for line input, speaker input, low impedance microphone, or high impedance microphone. There are provisions for the microphone inputs to be fed through; the microphone input connector is directly connected to an output connector. The microphone may be plugged into the unit and be directly connected to an output which can feed an audio amplifier while the signal is tapped off to feed into the inputs of the lighting control. Similarly the speaker right and left signals can be fed in and the out to speakers while the signal is tapped off for an input to the lighting control. 
     Item  40  in Embodiment 3 (See  FIG. 8 ), as in Embodiment 2, make use of the special amplifier from Analog Devices, SSM2167. As in Embodiment 2, there is a provision for operator adjustment of the noise floor, the level below which background noise will be rejected. As in Embodiment 2 there is provision for operator adjustment of the compression ratio. A selector switch is added for the setting of the response time of the AGC (automatic gain control). The preferred form of the present invention makes use of an integrated circuit amplifier that provides both compression and AGC operation. This can also be achieved by use of other components but, the choice of this integrated circuit amplifier simplifies the design. For some of the present invention embodiments the compression ratio is adjustable by the operator to suit their music or other applications. A compression ration of approximately 5:1 was selected for the present invention because it gives a pleasing response to music; for a 20 dB change in music this gives a variation in light intensity of about 6:1. 
     Item  380  is a bar graft indicator (See  FIG. 9 ). Embodiment 3 has a bar graph indicator added to display the signal level from amplifier  50  to aid the operator in set up. 
     Items  60 ,  70 ,  80  (See  FIG. 5 ). Instead of 3 band filters as used in the Preferred Form and in Embodiment 2, Embodiment 3 uses 7 switched capacitor filters. Each frequency band is narrower than in the Preferred Form or Embodiment 2. To accommodate these added filter bands a third divider is added to provide the clock frequencies needed. As in Embodiment 2 there is provision for operator adjustment of the clock frequency so that the bands filters can be moved up or down by an octave; by reducing the clock frequency by one half or by doubling the clock frequency. It is possible to have more than one clock, with each controlling different bands. 
     Items  150 ,  160 ,  170  are detectors (See  FIG. 4 ). There are seven detector circuits in Embodiment 3, one for each of the frequency bands. The detector circuits as in Embodiment 2 make use of operational amplifiers to produce full wave detection, item  171 , of the audio signals; thus producing better response time to the audio signals. Provisions in Embodiment 3 are provided for soft, medium or sharp response. For medium response capacitor  175  is added by switch  177  in response to a signal from item  280 . For soft response capacitor  176  is added in by soft response switch  178 . For sharp response capacitors  175  and  176  are not connected into the circuit. The response time is selected by an operator selector. 
     Items  310 ,  320 , and  330  are comparator (See  FIG. 1 ). There are seven comparators in Embodiment 3. 
     Item  340  (See  FIG. 9 ) is added in Embodiment 3. Item  340  is made up of switches and logic gates to provide selection of any or the seven frequency bands or the dimmer control to any of the 5 output drives. 
     Items  190 ,  200  and  210  are output drivers. Instead of three output drives as in the Preferred Form and in Embodiment 2 there are five output drivers in Embodiment 3. Each output driver is rated to 500 watts output and 1500 watts total power output. This power could be scaled to any power level. 
     Item  220  is an a.c. receptacle. Instead of 3 single ac outlet receptacles as in the Preferred Embodiment and Embodiment 2 there are 5 duplex ac outlets in Embodiment 3. This provides 10 ac outlets, 2 per output. The reference to 3 receptacles is only for reference and in no way limits the present invention in the number of receptacles used. 
     Embodiment 4 
     Embodiment 4 (See  FIG. 10A ) makes use of transistorized outputs, with pulse width modulation to provide a near unity input power factor instead of using triacs with phase control. Triacs and SCR&#39;s, depending on the degree to which they are phased on, have poor input power factor. When used as in the Preferred Form, and Embodiments 2 and 3 the input power factor will vary with the brightness of the lights, items  230 , connected to the outlets, items  190 ,  200 , and  210 . For higher powers it becomes more important to have a near unity power factor. Pulse width modulation also provides a near linear power output response to the audio signal. 
     Item  250 , the power supply for the control circuits provides a regulated positive 5 volts and a regulated minus 5 volts as in Embodiments 2 and 3, but it does not provide a sync signal as in the prior embodiments. 
     Item  180 , the ramp generator is not used in Embodiment 4. 
     Item  560  is a triangular wave generator, that provides a triangular output at the desired switching frequency of the output drivers, items  620 , and etc. (any number of outputs and output drivers could be provided.) This triangular wave provides the reference signal for the comparators. A saw-tooth wave could also be used instead of a triangular wave. The frequency of the triangular wave sets the output switching frequency. The switching frequency should be above the audio range that is above 20 KHz. 50 KHz is chosen as the switching frequency for Embodiment 4. The higher the switching frequency the smaller the components in the output filters, item  610 , can be; conversely the switching losses of the transistors, item  483 , and the snubbers, item  600 , will be. Two phase or three or more phase waveforms from item  560  with each applied to a different comparator provides a means of operating some of the output drivers items  620  can be made which would reduce the ripple current through the capacitor  623 . 
     Item  570  is an ac line filter. The purpose of this filter is to prevent transient voltages due to the switching of the output drive  620  from being fed back onto the ac power line. This is an LC (Inductor-Capacitor) filter. This filter is a commercially available item. 
     Item  440  is a bridge rectifier which converts the line voltage to a dc voltage. 
     Item  590  is a capacitor that provides a bypass for the switching currents between the plus and minus dc voltage output of item  580 . 
     Item  600  is a snubber circuit to reduce the switching transient voltages across the power transistor, item  623 . This snubber circuit is capacitor and resistor in series. It prevents the transient voltages caused by switching from becoming excessive and causing a failure of the transistor item  623 . 
     Item  610  is a filter for the output power to the output receptacles. This is an inductor-capacitor filter. This reduces the current ripple, at the switching frequency, to the output, item  220 . 
     Item  630  is an isolated power supply for providing the power for the driver integrated circuit, item  622 . 
     Item  620  (See  FIG. 13 ) is the output driver. Item  621  is a high frequency optical isolator (opto-isolator) integrated circuit which has fast response time. The input to the opto-isolator  621  is from the output of the comparator  310  through the output select logic  340 . The output of the opto-isolator item  621  is the input of the drive IC (integrated circuit) item  622 . Item  622  is provided power by the isolated power supply, item  630 . Item  622 , then provides the gate drive signal to the transistor  623  to control the turn on and turn off of this transistor in response to the signal from the opto-isolator. Item  623  is preferably an IGBT (Isolated Gate Bipolar Transistor). A MOSFET (Metal Oxide Semiconductor Field Effect Transistor) transistor could also be used. The output from driver item  620  is connected through the output filter item  610  to the output receptacle  230  to power the light  230  that is connected to this receptacle. 
     Embodiment 5 
     Embodiment 5 (See  FIG. 11 ) has outputs driving RGB (Red, Green, Blue) LED modules. The RGB modules used are Lamina BL-4000. 
     Items  340 ,  350  and  360  are buffer amplifiers. These buffer amplifiers are transistor emitter followers made up of and NPN transistor for pull up and a PNP transistor for pull down with an output resistor to prevent oscillation of the emitter followers. 
     Items  370 ,  380  and  390  (See  FIG. 14 ) are delay circuits  370 ,  380 , and  390  provide approximately a 1 millisecond delay in the signal to the drive circuit for one element of the drive for each RGB LED. The reason for the delay is that if all three signals to an RGB LED have equal on time then the color white is shown, So these delay circuits,  370 ,  380  and  390  are white suppression circuits so that the result is that the RGB LED lights  520 ,  530 , and  540  are more colorful in response to the audio signal. The rise of the signal from buffer Amp  340 , or  350  or  360  is delayed by the charge of capacitor  373  through resistor  371 . When the signal from the buffer amp  340  drops to zero the capacitor  373  is quickly discharged through diode  372 . Nand gate  374  is a gate with a Schmidt trigger input so that the signal switching out of nand gate  374  has a sharp rise and fall. Nand gate  374  inverts the signal so nand gate  375  is added to restore the polarity of the signal. The output from nand gate  375  goes to the selected drives  400  or  440  or  480 . 
     Item  550  is a power supply for the output drives  400  through  480 . This power supply provides a regulated positive 9 volts dc and a negative 5 volts dc. 
     Items  400  through  480  (See  FIG. 15 ) (Item  400  is taken as an example) The signal from the delay circuit  370  is input to the emitter follower transistors  401  and  402 . The NPN transistor  401  provides a rapid pull up and the PNP transistor  402  provides a rapid pull down, thus the signal from the emitters through resistor  403  is switched sharply in response to the input signal. Resistor  403  is a small resistor to prevent oscillations of the emitter followers  401  and  402 . Zener diode  404  drops the voltage from the output of the emitter followers by 5 volts so that when the output of the emitter followers  401  and  402  is low the MOSFET transistor  411 , and the NPN transistor  408  are both biased off. When the input signal is high the signal from the emitter followers through resistor  403  is high the voltage at the gate of MOSFET transistor  411  is raised to turn on transistor  411  on, this voltage will also turn on NPN transistor  408 . When transistor  408  turns on it switches 5 volts across resistor  409  and potentiometer  410 . Resistor  409  and potentiometer  410  set the current through transistors  408  and  411  and thus the current to the LED element to which they are connected. Diode  406  has approximately the same voltage across it as the emitter base junction of transistor  408 , so that the voltage at the base of transistor  408  is at about a plus 0.6 volts, This causes the full 5 volts from the negative 5 volt supply to be applied across resistor  409  and potentiometer  410 . The variation in the emitter base junction of transistor  408  with temperature is approximately matched by the variation in voltage with temperature of the voltage of diode  406  so that the current source is stable with temperature changes. Diode  412  provides a path for any reverse voltage that could by generated at the turn off of transistor  411 , such a reverse voltage would be created by any inductance in the output leads. This protects the transistor  411  from any excessive voltage transient when it is turned off. Potentiometer  410  provides a means of adjusting the output current of the drive. 
     Items  490 ,  500  and  510  are the output connectors for connecting the RGB LED&#39;s to the outputs. There are six possible variations in the connection of any of the RGB element. With the delay circuits,  370 ,  380  and  390  this provides 18 variations in the possible variations in the response of the RGB LED&#39;s  520 ,  530  and  540 . Since the selected RGB LED&#39;s used Lumina BL-4000 is such that each element uses the same current the RGB LED&#39;s could be connected in series will the connections changed, to have more RGB LED&#39;s driven with each out. This would provide 6 different colors going at the same time if each output was connected to 2 RGB LED&#39;s; or 9 different colors if each output was connected in this manner. Since there are 6 different possible connection configurations for an RGB LED, six variations could be connected to each output, this would provide 18 different colors since by reason of the delay circuits each would be different. Connecting additional RGB LED&#39;s in strings would require a higher voltage than the plus 9 volts from the power supply  550 , and the transistor  411  would be switching at a higher voltage and thus more power. 
     Items  520 ,  530  and  540  are three element RGB LED modules. Lumina BL-4000&#39;s are used since they are made with red, green and blue elements can all be operated at the same current levels. 
     Embodiment 6 
     Embodiment 6 (See  FIG. 16 ) is for use in an automobile or RV use from a 12 volt dc battery. This can be connected to the 12 volt dc line or the automobile or RV or can be connected to the cigarette lighter output, for low power lights. The output power drive is by PWM as in embodiment 4. Embodiment 6 uses 3 filter bands as in the Preferred Form. Item  250 , the power supply differs from the Preferred Form in that there is no transformer in the power supply nor does it produce a sync output. Item  250 , produces, output voltages of 8 volts dc, 5 volts dc and the 4 volt reference as in the Preferred Form. Item  180  the ramp generator is not used in Embodiment 6, instead the triangular wave generator item  560  is used, as in Embodiment 4. 
     Item  701  is the power switch for turning the power on and off. 
     Item  702  is an inductor, and  703  is a capacitor that form an input filter to keep switching transients, from the switching of transistor  411  from feeding back on the 12 volt dc supply wires. 
     Item  600  is the snubber as used in Embodiment 4; there is one of these for each of the 3 bands. 
     Item  610  is the output filter as used in Embodiment 4; there is one for each of the 3 bands. 
     Item  622  is the integrated circuit driver for driving the gate of the power transistor,  411 . The input signal is from the respective comparator output; there are 3 of these, one for each band. 
     Item  411  is an IGBT power transistor as used in Embodiment 4. A power MOSFET transistor could also be use as transistor  411 . 
     Item  704  is a two terminal jack to which the lights  705  can be connected, one for each band. 
     Item  705  is a 12 volt dc light or an arrangement of a number of 12 volt dc lights connected in parallel to each of the 3 outlets. This item could also be a string of LED&#39;s connected for 12 volt operation; again a number of 12 volt strings of LED&#39;s could be connected in parallel to each of the 3 outlets  704 . 
     Embodiment 7 
     Embodiment 7 (See  FIG. 17 ) is used to provide a drive signal such as a modulation signal for lasers. This embodiment does not use the comparators, and output drive, however, this embodiment may be added to any of the previous embodiments. There are 3, amplifier arrangements as shown in  FIG. 17  for 3 frequency bands as in the Preferred Form. Operation is not limited to 3 bands. Items  728 A and  7288  are a dual operational amplifier. Item  721  is a PNP transistor that in conjunction with resistor  722  provides a reference voltage that is equal to the zero voltage output of the detectors  150 ,  160 , and  170 . Amplifier  728 A is connected as a buffer amplifier to avoid loading down the detector circuits. Resistors  723 ,  724 ,  726  and  727  are all of equal value. Resistors  723 ,  724 ,  726 ,  727  and amplifier  728 B form a differential amplifier that has unity gain. Since transistor  721  and resistor provide a voltage that is equal to the zero output voltage of the detectors the voltage at the output of amplifier  7288  will be equal to the output of detectors that is referenced to ground instead of to about 3.5 volts. The resistor  725  is a low value of resistor to prevent capacitive loading by the cable connected to output jack  729  from causing instability of the amplifier  728 B. There are output jacks  729  for each band. For embodiment 7 as a variation of embodiments 2, 3, 4 or 5 the base of transistor  721  is connected to ground instead of to +4 volts and the bottom end of resistor  722  is connected to −5 volts, and the plus supply voltage is =5 volts instead of +8 volts. 
     In the development of the present invention the first problem encountered was that the dynamic range of response of the lights, visual was much smaller than the range of the audio signal. This dictated the need for compressing the audio signal, and the use of AGC to maintain the signal, this problem was solved with the discovery of a commercially available integrated circuit amplifier that met this requirement. 
     Another problem was that the an audio signal is typically shorter in time (because of the higher frequency of audio in relation to visual.) than the needed visual response; this problem was solved by use of a detector which captures the crest of the audio signal and stretches it so that it can be readily displayed. This response time was made selectable, by the operator, for a sharp or soft appearance of the lights. 
     Another problem was to have the output voltage to the lights have a linear response to the detected and stretched signal. This was achieved by creating a firing circuit for the output triacs that had a linear output voltage in relation to the signal. This is done by creating a ramp voltage that is synchronized with the zero crossings of the ac line voltage, then this ramp is compared with voltage comparators to the signal from the detector circuits. This is done in such a way the when the detector output voltage is low the triacs (SCR&#39;s could be used.) are turned on late in the ac voltage cycle to produce a correspondingly low output voltage, and when the detector output voltage is high the triacs are fired earlier in the ac voltage cycle. There is a slight deviation from linearity between the voltage from the detector output and the output voltage. 
     Another problem in the Embodiment 2 was how to easily vary the positions of the filter bands in frequency that is to keep the width of the midrange band while moving it in frequency that is to keep the width of the band at approximately an octave, but have the band at a different frequency. This problem was solved by using switched capacitor filters, which make use of a clock to set the frequency, the clock frequency setting was then made available to the operator. 
     This invention provides the lights connected to it a much improved response to the audio signals such as music. Triacs are used as the output device. Triacs can be controlled to conduct on both halves of the ac line. Thus the firing of the triacs is done at a 120 hertz rate, once during each half cycle of the ac line power. By controlling the timing of the firing of the output triacs in a more precise manner than previously used circuits and controlling the firing precisely for each half cycle this invention provides an improved response of the output voltage. Thus the lights show an improved response to audio signals such as music. The result of using the ramp and comparator is to have the output voltage be proportional to the audio signal from the detector, and a response of the lights to follow the audio in an improved manner; such as variations is loudness. Tests of the output voltage and power to the lights as the signal level was changed showed a nearly linear change of voltage and power as the signal level was changed. (The power in incandescent lights is nearly linear with voltage applied because of the resistance increasing with the heating of the filament.) 
     Controlling stage and theatrical lighting is one of countless ways that will display the present inventions power and versatility. The music industry is an all important way that the present invention will shine (sic) (see  FIGS. 16 &amp; 16A ). Examining stage and video productions show us that there is something seriously lacking in the results that lighting experts are accomplishing while they make their best attempts, with what technology they have, to visually stimulate their audience. This void, lacking in musical performances, lead the producers to throw every kind of flashing-moving-blinking-winking and nodding light arraignment and video enhancement in every which direction to accomplish something new and exciting, stimulating. 
     The main ability that is lacking in all lighting production is timing. In the musical stage lighting industry there has never been a lighting effect that correlates perfectly to the move of the music until the present invention. The present invention takes the guess work out of synchronization; because, the music generated controls the light intensity and the color variations. 
     Recreational lighting has become a very fast growing field. The present invention is not just a stage production tool but, it can bring the same visual professional stage effects to the home. People have invested 10&#39;s of thousand of dollars in stereo equipment; they will have a sound proof room, with one chair with only the equipment to stare at. With the present invention display panels could find placement within the room to enhance the sensory experience (see  FIGS. 29 ,  30  &amp;  35 ). The person who does not have the resources to invest a small fortune in room design will find that just stringing up Christmas type lights provide a phenomenal sensory experience. Even if one does not have their own the present invention, television music channels will now have more than Yule logs and fish tanks to put on their customers TV screens. 
     Recreational lighting, in the out of doors, might now consist of lighting up the back yard, pool or spa with the present invention (see  FIGS. 18 &amp; 18A ). The established competition is wide when it comes to pool/spa lighting but the controls, although patented, are very common place in the initial concept. With the present lighting systems there are limited choices as to color change modes. Whether using bulb, fiber-optics or Strobes the present invention brings an unprecedented change in how we perceive sound and lighting. We do not have to limit the control of lighting to the back yard. 
     Beyond the back yard and into the wide world of architecture is where there will be major competition in one-up-man-ship. Major buildings or structures will be transposed into frames for the imagination of man with a vision for the present invention building lobbies, business waiting rooms, or business advertisement will enhance the view of our world. (See  FIGS. 19 ,  19 A,  24 ,  32  &amp;  33 ). 
     The imagination in the use of the present invention will reach into major sporting venues and will generate quite a physiological phenomenon. People, at sports event release a beach ball amongst the crowd, or someone will start the “Wave” for participation. Now with large billboard size panels (see  FIGS. 20 &amp; 20A ), or the present invention being part of the scoreboard center piece (like in a basketball arena) the crowd will be part of a new generation of noise meter. The crowd will even work in unison to control the lights, or is the present invention controlling the crowd? 
     Whether inside or out, controlling the lighting system of a musical score, a dancing water display, the dance floor has long been a choice of special lighting effects. They are in for a change. The present invention is much more than just another sound activated, “follow the beat” product; there are no comparisons to the present invention (see  FIGS. 21 ,  22 ,  28 ,  28 A &amp;  28 B). Uses for the present invention are as endless as your imagination for home, recreation, and vehicle or, at work. 
     Vehicles (anything that transports) can receive an earth shaking transformation with the advent of the present invention. People, especially car buffs, have lit up their rides in various ways; some will change the bulb in their dome light, other hang light tubes under their vehicle or even mount lights in their wheel wells. The present selection of tube lighting have a pre-programmed series of patterns that the lights respond to; or, more generally, all, prior art in this field respond to the thumping of one particular frequency. The experience of a high end “Tuner” (specially equipped car) with a $30,000 audio system and the present invention is more than one could hope for until now (see  FIG. 25 ). 
     Many work desks have novelty items such as steel balls that bounce against themselves, things that balance or gyrate, basically things that a person can focus on briefly to take their mind somewhere else. The present invention and music linked with a small cube (see  FIG. 26 ) that has some colored lights within could be a great get away. Science might even find a therapeutic benefit to the link-up of music and the present invention. Early child development, when children are exposed to the present invention as an infant (see  FIG. 27 ), is uncharted waters. Science will find great interest in the effects of the present invention on mankind. 
     Staying with the work place thought. The present invention can be used by Human Resource departments to find just the right voice for greeting customers, or even a radio or T.V. personality (see  FIG. 26A ). When viewing many different voices with the present invention there is a pattern that consistently shows up; people with pleasing sounding voices will appear almost even across the board when using three color lighting set up. People that have a somewhat “off” voice will light up uneven portions on the lights. 
     One of the most outstanding uses for the present invention is as a sensory enhancement for the hearing impaired. The hearing impaired often will turn speakers face down (see  FIGS. 28 &amp; 28A ) to “feel” the musical beat and have regularly used lighting to enhance the musical experience (watch the movie “Mr. Holland&#39;s Opus”). Hearing impaired individuals will now be able to play an instrument to create a musical arrangement that is appealing to their inner sense of beauty. They will be able to not only feel the results of their playing the musical instrument but, will be able to see the results of their manipulation of the instruments own characteristics. 
     People in the most remote places of the world can experience their own cultural music with the present invention and a means of generating power.