Abstract:
A polar loop transmitter includes separate phase and envelope paths providing a linearizing scheme for an efficient non-linear power amplifier. Loop filters are included in each of the phase and envelope paths to enable the path characteristics to be matched to one another. A polar loop transmitter and other types of envelope elimination and restoration transmitters control the output envelope of the power amplifier by connecting the output of the envelope detector, or in an envelope feedback transmitter, the envelope error signal, to the bias control input of the power amplifier. The transmitter can further include compensation means for compensating for non-linearities in the envelope control means and a loss of feedback control detector to ensure that the feedback signal remains within acceptable limits.

Description:
FIELD OF THE INVENTION  
         [0001]    The present invention relates to transmitter circuits, particularly but not exclusively to power amplifier linearizing circuits such as envelope elimination and restoration transmitters and polar loop transmitters for use in portable communications devices such as mobile telephones.  
         BACKGROUND  
         [0002]    The present trend in portable communications devices such as mobile telephones is to increasingly lightweight devices with increased talk-time between battery recharge cycles. Such developments require ever more efficient radio-frequency (RF) amplifiers to minimise power consumption. In cellular systems such as GSM, the modulation scheme is a constant amplitude scheme, also referred to as constant envelope modulation, which permits use of efficient non-linear amplifiers. However, recent types of communication system such as EDGE and UMTS use non-constant envelope modulation schemes. The drawback is that the amplification of non-constant envelope RF signals requires the use of linear power amplifiers, which are inherently less efficient. The lower power efficiency of linear amplifiers translates into higher power consumption and higher heat dissipation.  
           [0003]    A variety of linearisation architectures and schemes exist, including fixed and adaptive pre-distortion, adaptive bias, envelope elimination and restoration, polar loop and Cartesian loop transmitters. Details of such devices are shown in “Increasing Talk-Time with Efficient Linear PA&#39;s”, IEE Seminar on TETRA Market and Technology Developments, Mann S, Beach M, Warr P and McGeehan J, Institution of Electrical Engineers, 2000, which is incorporated herein by reference. However, many of these devices and techniques are unsuitable for battery operated portable devices such as mobile telephones, or are incapable of meeting current RF design standards, such as the TETRA linearity standard, ETSI publication ETS 300 396-2; “Trans-European Trunked Radio (TETRA);-Voice plus Data (V+D)—Part 2: Air Interface (AI)”; March 1996.  
           [0004]    Envelope elimination and restoration (EER) transmitters separate envelope and phase information from an input modulated signal. The phase information is then passed through a power amplifier as a constant envelope signal, permitting the use of efficient, non-linear amplifiers, while the envelope signal is added to the power amplifier output. Such circuits suffer from the inherent problem that the phase and envelope information propagates through separate paths, which introduces different delays on the phase and envelope components before they are combined again at the output of the transmitter. This leads to distortion of the modulation.  
         SUMMARY OF THE INVENTION  
         [0005]    According to a first aspect of the invention, there is provided a polar loop transmitter comprising an envelope loop, a phase loop and means disposed within each of the phase and envelope loops configured to match the transfer characteristics of the phase and envelope loops. The matching means can comprise a loop filter in each of the phase and envelope loops. Each loop filter can be configured so that the transfer characteristics of the phase and envelope loops are matched over an operating frequency range of the transmitter circuit. For example, each loop filter can be configured so that the phase and envelope loops are of the same type and have substantially the same bandwidth and loop damping.  
           [0006]    The envelope loop can include envelope control means for the output signal from a power amplifier which forms part of the polar loop transmitter circuit. The envelope control means can comprise a power supply modulator arranged to modulate the voltage supply of the power amplifier or can be implemented by the connection of an envelope detector to a bias control input of the power amplifier.  
           [0007]    The polar loop transmitter according to the first aspect of the invention can further comprise compensation means disposed in the envelope loop for compensating for non-linearities in the envelope control means. It can further comprise a detector configured to detect loss of feedback control.  
           [0008]    According to a first aspect of the invention, there is further provided a polar loop transmitter comprising a power amplifier for amplifying an input signal having input phase and envelope components to produce an output signal having output phase and envelope components, an envelope loop including elements configured to produce an envelope difference signal representative of the difference between the input and output envelope components, said envelope loop having a loop transfer characteristic, a phase loop including elements configured to produce a phase difference signal representative of the difference between the input and output phase components, said phase loop having a loop transfer characteristic and elements disposed within each of the phase and envelope loops configured to match the transfer characteristics of the phase and envelope loops.  
           [0009]    According to a second aspect of the invention, there is provided an envelope elimination and restoration transmitter including a power amplifier having a bias control input, wherein the transmitter includes an envelope detector for detecting the envelope of an input signal and the output of the envelope detector is connected to the bias control input of the amplifier to control the output signal envelope.  
           [0010]    By removing the need for a power supply modulator, the switching noise and limited efficiency associated with such modulators is removed. In addition, cost savings can be achieved, while creating EER transmitters with improved efficiency for linear modulation schemes.  
           [0011]    The transmitter according to the second aspect can further comprise a slow power supply modulator configured to modulate the supply voltage to the power amplifier. The transmitter according to this aspect of the invention can include pre-distortion or envelope feedback to make the transmitter linear. Different solutions for the phase path such as offset loop and direct fractional synthesis can also be included.  
           [0012]    According to a third aspect of the invention, there is provided an envelope feedback transmitter including a power amplifier operable to provide an output signal, means for controlling the envelope of the output signal and compensation means for compensating for non-linear characteristics of the envelope control means.  
           [0013]    By combining tough and non-critical direct gain compensation with envelope feedback, high linearisation of the amplifier envelope transfer function can be achieved. This aspect of the invention can also be combined with any suitable solution for the phase path such as an offset loop or a direct fractional synthesis.  
           [0014]    The envelope control means can comprise a modulator for modulating the voltage supply of the power amplifier. Alternatively, the feedback transmitter can further comprise means for providing a difference signal representative of the difference between input and output envelope components, wherein the difference signal is connected to a bias control input of the power amplifier to provide the envelope control means. The difference signal can be connected to the bias control input of the power amplifier via a loop filter.  
           [0015]    The difference signal providing means can comprise a comparator arranged to receive signals from first and second envelope detectors for detecting the input and output envelope components respectively.  
           [0016]    The compensation means is disposed between the output of the amplifier and the input to the comparator. The compensation means can comprise first and second compensation elements, the first compensation element being disposed between the first envelope detector and a first input to the comparator and the second compensation element being disposed between the second envelope detector and a second input to the comparator. The first and second compensation elements can be configured to have a large signal transfer function which approximates to the inverse of the large signal transfer function of the envelope control means.  
           [0017]    The compensation means can also be disposed between the output of the comparator and the envelope control means. In this case, the compensation means can comprise a compensation element having a linear transfer function with variable gain and a non-linear gain control. The non-linear gain control can be connected to the output of either one of the first and second envelope detectors.  
           [0018]    According to a fourth aspect of the invention, there is provided a feedback transmitter having means for providing a difference signal representative of the difference between input and feedback signals, comprising a detector configured to detect a loss of feedback control when the difference signal exceeds a predetermined threshold.  
           [0019]    The feedback amplifier can be an envelope elimination and restoration transmitter, in which the detector comprises an amplitude detector configured to detect a loss of feedback control when the amplitude of the envelope error exceeds a predetermined threshold.  
           [0020]    The feedback amplifier can further comprise a power amplifier for amplifying an input signal having input phase and envelope components to produce an output signal having output phase and envelope components and an envelope loop including elements configured to produce an envelope difference signal representative of the difference between the input and output envelope components, wherein the amplitude detector is configured to monitor the difference signal.  
           [0021]    The feedback amplifier can also comprise a comparator for producing the difference signal, the comparator being configured to receive output signals from first and second envelope detectors.  
           [0022]    The feedback amplifier can alternatively be a Cartesian transmitter in which the difference signal is representative of the difference between in-phase I input and feedback signals or quaternary Q input and feedback signals.  
           [0023]    By detecting and acting on the loss of feedback control, the use of a circulator, or isolator, between the amplifier and impedance load is rendered unnecessary, so increasing efficiency and saving on cost.  
           [0024]    According to the fourth aspect of the invention, there is further provided a method of detecting a loss of loop control in a feedback transmitter providing a difference signal representative of the difference between input and output signal components, comprising monitoring the difference signal and detecting a difference signal deviation greater than a predefined threshold.  
           [0025]    The input and output signal components can comprise signal envelope components. The step of detecting a difference signal deviation can comprise detecting a difference signal amplitude greater than a predefined threshold.  
           [0026]    The method can further include averaging the difference signal. 
       
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS  
       [0027]    Embodiments of the invention will now be described by way of example with reference to the accompanying drawings, in which:  
         [0028]    [0028]FIG. 1 is a perspective view of a mobile telephone handset;  
         [0029]    [0029]FIG. 2 is a schematic diagram of mobile telephone circuitry for use in the telephone handset of FIG. 1;  
         [0030]    [0030]FIG. 3 illustrates the basic principle of an envelope elimination and restoration transmitter (EER);  
         [0031]    [0031]FIG. 4 shows an envelope feedback transmitter;  
         [0032]    [0032]FIG. 5 shows a polar loop transmitter in accordance with the invention;  
         [0033]    [0033]FIG. 6 is a schematic diagram of an EER transmitter using a bias input of a power amplifier in accordance with a second aspect of the invention;  
         [0034]    [0034]FIG. 7 is a schematic diagram of the transmitter of FIG. 6 with the addition of a slow modulator;  
         [0035]    [0035]FIG. 8 is a schematic diagram of a first arrangement of an envelope feedback transmitter in accordance with a third aspect of the invention;  
         [0036]    [0036]FIG. 9 is a schematic diagram of a second arrangement of an envelope feedback transmitter in accordance with a third aspect of the invention;  
         [0037]    [0037]FIG. 10 is a schematic diagram of the envelope feedback transmitter of FIG. 8 with the addition of a phase offset loop;  
         [0038]    [0038]FIG. 11 is a schematic diagram of an envelope feedback transmitter with loss of feedback control detection according to a fourth aspect of the invention; and  
         [0039]    [0039]FIG. 12 is a flowchart illustrating the operation of the transmitter of FIG. 11.  
     
    
     DETAILED DESCRIPTION  
       [0040]    Referring to FIG. 1, a mobile station in the form of a mobile telephone handset  1  includes a microphone  2 , keypad  3 , with soft keys  4  which can be programmed to perform different functions, an LCD display  5 , a speaker  6  and an antenna  7  which is contained within the housing.  
         [0041]    The mobile station  1  is operable to communicate through cellular radio links with individual public land mobile networks (PLMNs) operating according to communication schemes such as UMTS and EDGE.  
         [0042]    [0042]FIG. 2 illustrates the major circuit components of the telephone handset  1 . Signal processing is carried out under the control of a digital micro-controller  9  which has an associated flash memory  10 . Electrical analogue audio signals are produced by microphone  2  and amplified by pre-amplifier  11 . Similarly, analogue audio signals are fed to the speaker  6  through an amplifier  12 . The micro-controller  9  receives instruction signals from the keypad and soft keys  3 ,  4  and controls operation of the LCD display  5 .  
         [0043]    Information concerning the identity of the user is held on a smart card  13  in the form of a GSM SIM card which contains the usual GSM international mobile subscriber identity (IMSI) and an encryption key KI that is used for encoding the radio transmission in a manner well known per se. The SIM card is removably received in a SIM card reader  14 .  
         [0044]    The mobile telephone circuitry includes a codec  15  and an rf stage  16  including a power amplifier stage  17  feeding the antenna  7 . The codec  15  receives analogue signals from the microphone amplifier  11 , digitises them into an appropriate signal format and feeds them to the power amplifier stage  17  in the rf stage  16  for transmission through the antenna  7  to the PLMN shown in FIG. 1. Similarly, signals received from the PLMN are fed through the antenna  7  to be demodulated in the rf stage  16  and fed to codec  15 , so as to produce analogue signals fed to the amplifier  12  and speaker  6 .  
         [0045]    Referring to FIG. 3, the power amplifier stage  17  comprises an envelope elimination and restoration (EER) transmitter  18  which separates the envelope and phase components of an input modulated RF signal into two separate paths  19 ,  20 . The envelope path  19  includes an envelope detector  21  which extracts amplitude information from the RF input signal and an envelope controller  22  connected to a power amplifier  23 . The phase path  20  includes a limiter  24  which eliminates the input signal envelope to generate a constant amplitude phase signal. The phase signal output of the limiter is fed to an RF input of the amplifier  23  via a variable delay module  25 , while the amplitude information is used to control the output envelope via the envelope controller  22 . The amplitude and phase information are therefore recombined via the power amplifier  23  to produce the RF output for the antenna  7 . The envelope controller  22  is for example a fast power supply modulator which directly modulates the supply voltage of the power amplifier  23 . The purpose of the delay module  25  is to compensate for the difference between envelope and phase path delays. However, this solution changes the loop characteristics and stability making it difficult to control. This is especially the case if a high bandwidth is needed for wideband modulation schemes such as the 8-PSK modulation used in EDGE, since the insertion of a delay can only match the loop transfer functions over a relatively narrow frequency band. Furthermore, it is difficult to ensure that the delay tracks loop changes with temperature and other variable conditions.  
         [0046]    The addition of envelope feedback to the circuit of FIG. 3 leads to an envelope feedback transmitter  26 , shown in FIG. 4. In general terms, the envelope feedback transmitter  26  works by comparing the output envelope with the input envelope and using the difference signal to control a power amplifier, thereby providing improved linearity. The envelope loop of the envelope feedback transmitter  26  comprises first and second envelope detectors  27 ,  28 , the respective outputs of which are fed to the respective inputs of a comparator  29 . The output of the comparator  29  is fed to a loop filter  30  and then via an envelope controller  31  to a voltage supply terminal  32  of a power amplifier  33 . The phase loop of the envelope feedback transmitter is shown in its simplest form as comprising a limiter  34  which is fed with the RF input signal and has its output connected to an RF input  35  of the power amplifier  33 . Since envelope feedback on its own does not correct AM-PM distortion, phase feedback is added to the circuit of FIG. 4 to provide an improved transmitter known as a polar loop transmitter or polar feedback transmitter  36 , as shown in FIG. 5.  
         [0047]    As well as comparing the input and output envelopes, the polar feedback transmitter compares the phases of the input and output signals and uses the resulting phase error to drive a voltage controlled oscillator.  
         [0048]    As described above in relation to FIG. 4, the envelope loop of the polar feedback transmitter  36  of FIG. 5 comprises first and second envelope detectors  27 ,  28 , the respective outputs of which are fed to the respective inputs of the comparator  29 . The output of the comparator  29  is fed to a first loop filter  30  and then via the envelope controller  31  to the voltage supply terminal  32  of the power amplifier  33 . As mentioned above, the envelope controller  31  is, for example, a switching power supply which directly modulates the supply voltage of a switched mode power amplifier  33 . The phase loop of the transmitter  36  comprises first and second limiters  37 ,  38  for producing a constant amplitude phase signal and a phase detector  39  for deriving a difference signal from the outputs of the limiters  37 ,  38 . The output of the phase detector  39  is fed via a second loop filter  40  to a voltage controlled oscillator (VCO)  41 , and then fed to an RF input  42  of the power amplifier  33 . The output of the power amplifier  33  is mixed with a local oscillator signal  43  at a mixer  44  to shift the carrier frequency to an intermediate frequency and fed back through a low pass filter  45  as an input to the first envelope detector  27  and the second limiter  38 . The purpose of the low pass filter  45  is to remove sideband components and local oscillator leakage from the mixed signal. The inputs to the second envelope detector  28  and the first limiter  37  are provided by the RF input signal.  
         [0049]    The first and second loop filters  30 ,  40  are configured so that the loop characteristics of the phase and envelope loops are the same or very similar, with respect to both phase delay and gain, over the range of operating frequencies of the transmitter circuit. For example, both are type II loops with two poles at zero and both have the same bandwidth and loop damping. This results in similar group delays in the two loops, limiting the delay difference between the phase and envelope components.  
         [0050]    In a second aspect of the invention illustrated in FIG. 6, a power supply modulator is not used to control the power supply of the power amplifier. The EER transmitter  46  comprises an envelope detector  47  which receives the input signal, the output of which is connected to the bias control input  48  of a power amplifier  49 . In traditional non-EER transmitters, the bias control input is used to set the transmitter power level, while any envelope information is contained in the normal RF input signal to the power amplifier. In the phase loop, the input signal is connected via a limiter  50  to the RF input  51  of the amplifier  49 . Comparing this circuit with the circuit of FIG. 3, it is apparent that this configuration obviates the need for a separate envelope controller.  
         [0051]    While described above with reference to FIG. 6, the invention can be implemented in any EER transmitter architecture, including different solutions for the phase path such as offset loop and direct fractional synthesis. The transfer function for the bias control input to power amplifier envelope is generally non-linear. To make the transmitter linear, either pre-distortion or envelope feedback can be used. For example, the envelope controller  31  in FIGS. 4 and 5 can be omitted by using a bias control input on the power amplifier  33 .  
         [0052]    Referring to FIG. 7, this aspect of the invention can be combined with a slow power supply modulator  52 , which has less switching noise problems than a fast power supply modulator and which can be implemented with higher efficiency. The modulator  52  is connected to a supply voltage terminal  53  of the power amplifier  49  and is used to set an optimum power supply voltage for a given output power level, while the bias control arrangement  47 ,  48  according to the second aspect handles the envelope variation due to modulation.  
         [0053]    In a third aspect of the invention, compensation elements are added to EER circuits to compensate for non-linearities in the amplifier envelope control means.  
         [0054]    Amplifier envelope control can be achieved using a variety of techniques, for example direct modulation of the amplifier supply voltage using a switched mode power supply or regulator, by controlling the bias conditions of the amplifier as described in relation to the second aspect above, by adding a variable gain amplifier on the input of the main amplifier or any combination of these.  
         [0055]    Referring back to the circuit of FIG. 4, a compensation element can be added in two different places within the envelope loop. The first is between the output of the amplifier  33  and the input to the comparator  29 , which requires a corresponding compensation element in the input path. The second is between the comparator  29  and the amplifier envelope control mechanism  31 .  
         [0056]    [0056]FIGS. 8 and 9 illustrate one way to place the compensating elements  55 ,  56 ,  57 . The element referencing has been retained from that of FIG. 4 and the description of the overall circuit operation is the same. The compensation elements  55 ,  56  in the circuit of FIG. 8 are designed to have a large signal transfer function which approximates to the inverse of the envelope controller large signal transfer function. The compensation element  57  in the circuit of FIG. 9 is designed to have a linear transfer function using a variable gain amplifier  58  and a non-linear gain control  59 . The gain in the compensation element  57  is then controlled by feeding the envelope information from one of the envelope detectors  28  forward to the gain control input of the compensation element. The non-linearity in the gain control  59  approximates to the inverse of the first derivative of the large signal transfer function of the envelope controller, or, in other words, approximates to the inverse of the envelope controller small signal gain as a function of the required envelope.  
         [0057]    The exact shape of the non-linearity used to compensate the amplifier envelope control transfer function is not critical. It can, for example, be a piecewise linear characteristic, be comprised of exponential, linear and logarithmic segments, or hyperbolic tangent segments. The principle is to keep the resulting loop gain within boundaries, for example in the range  1 : 3  to  1 : 15 , being the ratio between minimum and maximum loop gain over the modulation envelope variation, that allow the loop to compensate the remaining non-linearities without excessive requirements on loop gain and without excessive variation in loop characteristics as a result of the non-linearities.  
         [0058]    The phase signal for this aspect of the invention can be generated in any way that is suitable for the specific modulation and system. Examples are an offset loop as shown in FIG. 10 and direct synthesis of the phase modulated RF signal using a fractional synthesis. The elements of FIG. 10 correspond to those shown and described in relation to FIG. 5, with the addition of the compensation element  57 .  
         [0059]    In normal operation, the output signal of the comparator in the envelope loop of an envelope feedback amplifier has a limited amplitude. However, the signal increases significantly in amplitude if the amplifier output envelope does not follow the input signal amplitude, for example due to clipping or saturation of the amplifier output stage, resulting in loss of feedback control. Clipping or saturation can occur as a result of an impedance mismatch and reflections caused, for example, by changes in the impedance of the antenna to which the amplifier output is connected.  
         [0060]    [0060]FIG. 11 shows the EER transmitter of FIG. 4, with the addition of an amplitude detector  60  at the output of the comparator  29  in the envelope loop. All of the other elements shown and the general operation of the circuit are described above with reference to FIG. 4. The operation of the detector  60  is described below with reference to the flowchart in FIG. 12. A detection threshold is first set (step s 1 ). This is set to be above the normal expected signal amplitude. The output of the comparator  29  is then continuously monitored (step s 2 ) and the output averaged over a given period (step s 3 ), to avoid detection of spurious amplitude spikes. If a loss of loop control is detected by the averaged comparator output signal exceeding the threshold for a given period (step s 4 ), appropriate action is taken to remedy the problem (step s 5 ).  
         [0061]    The action to be taken depends on the cause of the loss of control. For example, if this is due to clipping or saturation in the amplifier output stage, the output power is lowered, avoiding modulation distortion at the cost of lower transmitted power. The loss of control detection can also be used to change the bias conditions or power supply of the amplifier, enabling it to cope with changes in load impedance. Modulation distortion can then be avoided while output power is maintained, at the possible cost of additional power consumption in the amplifier.  
         [0062]    Detection can also be carried out at later stages in the forward envelope path, for example at nodes in the loop filter, or at any point at which the signal used for detection represents the envelope error and not the actual envelope.  
         [0063]    While it has been described with respect to an envelope feedback amplifier, this aspect of the invention can also be used in other types of transmitter circuit, including a Cartesian feedback transmitter where detection can be done on the in-phase I or quaternary Q signal components. I and Q signals are generated in the feedback loop using a quadrature demodulator and compared directly to the wanted I and Q signals. The error signal from this comparison can be used to detect loss of control, in the same way as the error signal from the amplitude comparison in the polar loop architecture.  
         [0064]    It will be understood that instead of separating the envelope and phase components in the input signal by envelope detection and limiting, as shown in the accompanying figures, the input signal can be directly supplied as polar phase and envelope components.