Abstract:
A control circuit and method are provided for a flyback converter converting an input voltage to an output voltage, to compensate for an entry point of a burst mode of the flyback converter, so that the entry point is not affected by the input voltage, and audible noise resulted from a higher input voltage is reduced without impacting the light load efficiency of the flyback converter.

Description:
FIELD OF THE INVENTION 
       [0001]    The present invention is related generally to a flyback converter and, more particularly, to a control circuit and method for a flyback converter. 
       BACKGROUND OF THE INVENTION 
       [0002]    All electrical devices are required a power source for operation. Among the various types of power supplies, switching power converters are widely used because they have better efficiency and provide suitable output modulation. However, when a switching power converter is under light load conditions, its efficiency will reduce due to switching loss. To improve the efficiency at light load, a burst mode strategy is applied to reduce the average switching frequency and save the switching loss.  FIG. 1  is a perspective diagram of a conventional current mode flyback converter  10 , in which a rectifier  12  converts an AC voltage Vac into a DC input voltage Vin, a controller  16  detects the current flowing through a power switch  18  to obtain a current sense signal Vcs, and provides a control signal V GATE  according to the current sense signal Vcs and a feedback signal Vcomp to switch the power switch  18 , so as to have a transformer  14  to convert the input voltage Vin into an output voltage Vo, and an opto-coupler  20  generates the feedback signal Vcomp according to the output voltage Vo to feed back to the controller  16 . The feedback signal Vcomp is a function of the output voltage Vo. 
         [0003]      FIG. 2  is a perspective diagram of a portion of the controller  16  shown in  FIG. 1 , in which a burst circuit  22  has a hysteresis comparator  24  to generate a mask signal Smask according to the feedback signal Vcomp and a preset voltage Burst_level to mask a clock CLK by an AND gate  26 , and a pulse width modulation (PWM) circuit  28  has a comparator  30  to compare the current sense signal Vcs with the feedback signal Vcomp to generate a comparison signal Sc, and a flip-flop  32  to generate the control signal V GATE  according to the output of the AND gate  26  and the comparison signal Sc.  FIG. 3  is waveform diagram of the flyback converter  10  shown in  FIG. 1 , in which waveform  34  represents the load, waveform  36  represents the feedback signal Vcomp, and waveform  38  represents the control signal V GATE . Referring to  FIGS. 2 and 3 , in normal operation, i.e. the load is heavy, as between time t 1  and time t 2 , the feedback signal Vcomp is greater than voltages V BURH  and V BURL , as shown by the waveform  36 , so that the clock CLK is not masked, and in consequence the control signal V GATE  is continuously provided to switch the power switch  18 , as shown by the waveform  38 . The voltages VBURH and VBURL are hysteresis boundaries generated by the hysteresis comparator  24  according to the voltage Burst_level. At time t 2 , the load turns from heavy to light so that the feedback signal Vcomp begins to drop. When the feedback signal Vcomp is lower than the voltage V BURL , as shown at time t 3 , the flyback converter  10  enters a burst mode, in which the mask signal Smask will switch to logic “0” when the feedback signal Vcomp is lower than the voltage V BURL , thus masking the clock CLK, and the mask signal Smask will not switch to logic “1” until the feedback signal Vcomp is higher than the voltages V BURH , as shown at time t 4 . The clock CLK is released when the mask signal Smask switches to logic “1”. Hence, a burst cycle is generated to regulate the output voltage Vo and supply sufficient output power. One burst cycle is shown in  FIG. 3  as between time t 3  and time t 5 . 
         [0004]      FIG. 4  is a perspective diagram of the current sense signals Vcs under different input voltages Vin, in which waveform  40  represents the feedback signal Vcomp, waveform  42  represents the current sense signal Vcs corresponding to a high input voltage Vin, and waveform  44  represents the current sense signal Vcs corresponding to a low input voltage Vin.  FIG. 5  is a perspective diagram of burst mode entry points under different input voltages Vin, in which waveform  46  represents the voltage V BRUH , waveform  48  represents the voltage V BRUL , waveform  50  represents the feedback signal Vcomp corresponding to a high input voltage Vin, and waveform  52  represents the feedback signal Vcomp corresponding to a low input voltage Vin. Referring to  FIG. 4  in conjunction with  FIG. 1 , if the input voltage Vin is a higher one, the current sense signal Vcs increases at a higher speed, as shown by the waveform  42 ; if the input voltage Vin is a lower one, the current sense signal Vcs increases at a lower speed, as shown by the waveform  44 . After the current sense signal Vcs reaches the level of the feedback signal Vcomp, a propagation delay time Tp due to the delay in signal propagation must elapse before the power switch  18  is turned off. In addition, since the current sense signal Vcs increases at a higher speed under a higher input voltage Vin, the current sense signal Vcs corresponding to the higher input voltage Vin has a higher peak than the current sense signal Vcs corresponding to the lower input voltage Vin. In other words, the peak of the current I 1  in the primary side of the transformer  14  is higher under the higher input voltage Vin than under the lower input voltage Vin. In the burst mode, the current I 1  has a minimum pulse: 
         [0000]        I 1min=(Burst_level/ Rcs )+( V in/ Lm )× Tp,   [EQ-1] 
         [0000]    where Lm is magnetizing inductance. After the flyback converter  10  enters the burst mode, the average frequency of each burst cycle falls within an audible noise range of 100 Hz to 20 kHz, such that the higher the current I 1  is, the louder the audible noise will be. Moreover, the feedback signal Vcomp varies with the peak value of the current I 1 . Referring to  FIG. 5 , if the input voltage Vin is higher, the peak value of the current I 1  is higher and in consequence the feedback signal Vcomp is lower, as shown by the waveform  50 . Hence, the flyback converter  10  enters the burst mode earlier. On the contrary, if the input voltage Vin is lower, the peak value of the current I 1  is lower so that the feedback signal Vcomp is higher, as shown by the waveform  52 . As a result, the entry point B of the burst mode under the lower input voltage Vin comes later than the entry point A of the burst mode under the higher input voltage Vin. 
         [0005]    Therefore, it is desired an apparatus and method to compensate the propagation delay and thus compensate for the entry point of the burst mode. 
       BRIEF SUMMARY OF THE INVENTION 
       [0006]    An object of the present invention is to provide a control circuit and method for a flyback converter to compensate the propagation delay and thereby compensate for the entry point of the burst mode of the flyback converter. 
         [0007]    According to the present invention, a control circuit for a flyback converter including a transformer connected with a power switch switched by a control signal for the transformer to convert an input voltage into an output voltage, comprises a burst circuit to determine whether or not the flyback converter to enter a burst mode according to a feedback signal and a preset value, a compensator to compensate the feedback signal to generate a compensated feedback signal, and a pulse width modulation circuit to generate the control signal according to the compensated feedback signal and a current sense signal. The feedback signal is a function of the output voltage, and the current sense signal is a function of a current flowing through the power switch. The compensator compensates the feedback signal to prevent an entry point of the burst mode from being affected by the input voltage. 
         [0008]    According to the present invention, a control circuit for a flyback converter including a transformer connected with a power switch switched by a control signal for the transformer to convert an input voltage into an output voltage, comprises a burst circuit to determine whether or not the flyback converter to enter a burst mode according to a feedback signal and a preset value, a compensator to compensate a current sense signal to generate a compensated current sense signal, and a pulse width modulation circuit to generate the control signal according to the feedback signal and the compensated current sense signal. The feedback signal is a function of the output voltage, and the current sense signal is a function of a current flowing through the power switch. The compensator compensates the current sense signal to prevent an entry point of the burst mode from being affected by the input voltage. 
     
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         [0009]    These and other objects, features and advantages of the present invention will become apparent to those skilled in the art upon consideration of the following description of the preferred embodiments of the present invention taken in conjunction with the accompanying drawings, in which: 
           [0010]      FIG. 1  is a perspective diagram of a conventional current mode flyback converter; 
           [0011]      FIG. 2  is a perspective diagram of a portion of the controller shown in  FIG. 1 ; 
           [0012]      FIG. 3  is waveform diagram of the flyback converter shown in  FIG. 1 ; 
           [0013]      FIG. 4  is a perspective diagram of current sense signals under different input voltages; 
           [0014]      FIG. 5  is a perspective diagram of burst mode entry points under different input voltages; 
           [0015]      FIG. 6  is a perspective diagram of a first embodiment according to the present invention; 
           [0016]      FIG. 7  is a perspective diagram of the details of the control circuit shown in  FIG. 6 ; 
           [0017]      FIG. 8  shows a waveform diagram of a sawtooth wave; 
           [0018]      FIG. 9  is a waveform diagram of a compensated feedback signal and the current sense signals Vcs under different input voltages; and 
           [0019]      FIG. 10  is a perspective diagram of a second embodiment according to the present invention. 
       
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
       [0020]      FIG. 6  is a perspective diagram of a first embodiment according to the present invention. The controller  16  shown in FIG.  2  is now replaced by the control circuit  54  shown in  FIG. 6  to be used in  FIG. 1 . In the control circuit  54 , a compensator  56  compensates the feedback signal Vcomp to generate a compensated feedback signal Vcomp_c, a burst circuit  58  generates a mask signal Smask according to the feedback signal Vcomp and the preset voltage Burst_level to determine whether or not the flyback converter  10  to enter the burst mode, and a PWM circuit  60  generates the control signal V GATE  according to the current sense signal Vcs, the compensated feedback signal Vcomp_c, and the mask signal Smask, to switch the power switch  18 .  FIG. 7  is a perspective diagram of the details of the control circuit  54  shown in  FIG. 6 . As shown in  FIG. 7 , the compensator  56  includes an adder  62  having a positive input  622  to receive the feedback signal Vcomp, a negative input  624  to receive a sawtooth wave Sramp synchronous with the clock CLK, and an output  626  to generate the compensated feedback signal Vcomp_c. Since the higher the input voltage Vin is, the greater the propagation delay and the higher the peak of the current I 1  will be, the sawtooth wave Sramp is deducted from the feedback signal Vcomp so that the compensated feedback signal Vcomp_c has a right slope. The burst circuit  58  includes a hysteresis comparator  64  to generate the mask signal Smask according to the feedback signal Vcomp and the voltage Burst_level, and provide the mask signal Smask to an AND gate  66  to mask the clock CLK and in consequence reduce the number of times the power switch  18  is to be switched. The PWM circuit  60  includes a comparator  68  to compare the current sense signal Vcs with the compensated feedback signal Vcomp_c to generate a comparison signal S 2 , and a flip-flop  70  having a set input S to receive the output S 1  of the AND gate  66 , a reset input R to receive the signal S 2 , and an output Q to generate the control signal V GATE . 
         [0021]      FIG. 8  is a waveform diagram of the sawtooth wave Sramp, which has a width W equal to 6.25% of the switching cycle of the power switch  18  and a peak-to-valley difference H approximately equal to 0.15 V.  FIG. 9  is a waveform diagram of the compensated feedback signal Vcomp_c and the current sense signals Vcs under different input voltages Vin, in which waveform  72  represents the compensated feedback signal Vcomp_c, waveform  74  represents the current sense signal Vcs corresponding to a higher input voltage Vin, and waveform  76  represents the current sense signal Vcs corresponding to a lower input voltage Vin. In this embodiment, the difference between the highest value and the lowest value of the compensated feedback signal Vcomp_c is about 0.15 V, and the compensated feedback signal Vcomp_c has a right slope. If the input voltage Vin is a higher one, the current sense signal Vcs increases at a higher speed, as shown by the waveform  74 , and consequently the compensated feedback signal Vcomp_c is lower for the current sense signal Vcs under the higher input voltage Vin to reach. On the contrary, if the input voltage Vin is a lower one, the current sense signal Vcs increases at a lower speed, as shown by the waveform  76 , so that the compensated feedback signal Vcomp_c is higher for the current sense signal Vcs under the lower input voltage Vin to reach. Since the current sense signal Vcs under the higher input voltage Vin only has to increase to the lower level to reach the compensated feedback signal Vcomp_c, and the current sense signal Vcs under the lower input voltage Vin has to increase to the higher level to reach the compensated feedback signal Vcomp_c, the peak values of the current sense signals Vcs in both cases are substantially the same after the propagation delay Tp. In other words, be the input voltage Vin high or low, the current I 1  flowing through the power switch  18  will remain substantially the same, and the propagation delay is thus minimized. 
         [0022]    After the feedback signal Vcomp is compensated with the sawtooth wave Sramp, the current I 1  flowing through the power switch  18  under different input voltages Vin stays substantially the same. As a result, the entry point of the burst mode no longer changes with the variation of the input voltage Vin, and the propagation delay is reduced to minimum. Besides, in the burst mode, the peak value of the current I 1  will not rise because of a higher input voltage Vin, so that the audible noise is decreased. 
         [0023]      FIG. 10  is a perspective diagram of a second embodiment according to the present invention, in which a control circuit  80  also includes the burst circuit  58 , the PWM circuit  60  and the AND gate  66 . The control circuit  80  further includes a compensator  82  to compensate the current sense signal Vcs to generate a compensated current sense signal Vcs_c. The comparator  68  in the PWM circuit  60  compares the compensated current sense signal Vcs_c with the feedback signal Vcomp to generate the signal S 2 , which is then supplied to the reset input R of the flip-flop  70 . The compensator  82  includes an adder  84  having two positive inputs  842  and  844  to receive the current sense signal Vcs and the sawtooth wave Sramp respectively, and an output  846  to provide the compensated current sense signal Vcs_c. Similarly, after the current sense signal Vcs is compensated with the sawtooth wave Sramp, the peak value of the current I 1  flowing through the power switch  18  will remain substantially the same under different input voltages Vin, so that the entry point of the burst mode will not change as the input voltage Vin varies. 
         [0024]    While the present invention has been described in conjunction with preferred embodiments thereof, it is evident that many alternatives, modifications and variations will be apparent to those skilled in the art. Accordingly, it is intended to embrace all such alternatives, modifications and variations that fall within the spirit and scope thereof as set forth in the appended claims.