Abstract:
Methods and systems for frequency generation may comprise in a low-noise block down-converter (LNB) comprising an analog-to-digital converter (ADC) and a channel stacking switch (CSS): receiving a first satellite signal centered at a first frequency; receiving a second satellite signal centered at a second frequency; combining the first and second satellite signals to form a combined signal; the analog-to-digital converter transforming the combined signal from an analog signal to a digital signal; providing the digital signal to the CSS; receiving a third satellite signal centered at a third frequency; receiving a fourth satellite signal centered at a fourth frequency; translating the third satellite signal to a fifth frequency, combining the translated third satellite signal with fourth satellite signals to form a second combined signal; a second analog-to-digital converter transforming the combined signal from an analog signal to a second digital signal; and providing the second digital signal to the CSS.

Description:
TECHNICAL FIELD 
       [0001]    The disclosed technology relates generally to satellite communications, and more particularly, some embodiments relate to improved signal processing techniques for satellite signals. 
       DESCRIPTION OF THE RELATED ART 
       [0002]    Satellite television and other satellite communications have become mainstream in today&#39;s society. For example, satellite dishes and outdoor receiver units are common sights in commercial and residential areas.  FIG. 1  is a diagram illustrating a typically outdoor unit. Referring to  FIG. 1 , a satellite receiver outdoor unit (ODU)  110  typically comprises a dish antenna  150 , one or more antenna feed horns  130 , one or more low noise amplifier and block down converters (LNB)  140 , and an optional multiport cross point switch  160 . Dish  150  collects and focuses received signal power onto antenna feed horns  130  which couples the signal to LNBs  140 . A single dish  150  may have multiple feed horns  130  wherein each feed receives a signal from a different satellite in orbit. An installation may have more than one dish, feed, and LNB assemblies. The cross point switch  160  allows connection of the outdoor unit  110  to more than one integrated receiver decoder (IRD)  180  located inside the building. IRDs are commonly called set top boxes (STBs) arising from their typical installed location on top of TV sets. The LNB  140  converts the signal transmitted by a satellite in Earth orbit, for example C band, Ku band, or another frequency band, to a lower intermediate frequency (IF) suitable for transmission through coax inside a building. For example, L band IF (950 to 1450 MHZ) with RG-6 or RG-11 coax cable is commonly used. The IRD  180  tunes one transponder channel, demodulates the IF signal from the LNB down to base band, provides channel selection, conditional access, decodes the digital data to produce a video signal, and generates an RF output to drive a television. 
         [0003]    A satellite outdoor unit may have as many as three or more LNBs each with two receiving polarizations. The received polarization is selected by sending a voltage or other control signal to the LNB. In this configuration, six possible 500 MHz signals may be selected by the multiport cross point switch to be routed to each IRD. The 500 MHz signal is typically comprised of 16 transponder signals of 24 MHz bandwidth each with a guard band in between each transponder signal. Other transponder bandwidths may be used, such as 36 MHz or 54 MHz (either a single channel or shared by two TV signals) and 43 MHz. 
         [0004]      FIG. 2  is a diagram illustrating an example implementation of a low noise block  140 . In this example, the low noise block LNB receives horizontally and vertically polarized signals from the satellite. For each polarization, low noise block includes one or more low noise amplifiers (LNA)  141  to amplify the received signal to an acceptable level for processing. Preferably, the amplification may be done as close to the signal source (e.g., the antenna) as possible to avoid amplifying additionally introduce noise. The amplified received signal can be passed through a bandpass filter  142  to filter out unwanted noise from the signal. A down converter  143  can be used to downconvert the received signal to an intermediate frequency or directly to a desired frequency for distribution. In this example, the down converter includes a mixer and a local oscillator at the desired frequency (e.g., 9.75 GHz or 10.6 GHz). The downconverted signal can be further filtered and amplified prior to distribution. This is illustrated by low pass filter (LPF)  144  and amplifier (AMP)  146 . Switches  147  can be provided to allow selection and placement of the desired signal onto a selected output. Additional amplifiers  148  can also be provided for distribution of the signals such as, for example, along the cable drop. A switch control module  149  can also be provided to control selection of the matrix which is  147 . Switch control, for example, can respond to commands from the set top boxes to ensure delivery of desired program content accordingly. 
         [0005]      FIG. 3  is a diagram illustrating another example of a low noise block (LNB)  140 . The example illustrated in  FIG. 3  in particular is an example of a wideband LNB. Similar to the example illustrated in  FIG. 2 , this LNB  140  includes low noise amplifiers  141 , and pass filters  142 , downconverters  143 , and low pass filters  144 . However, because the example of  FIG. 3  is a wideband system, the output for each polarization (horizontal and vertical) or on a single output, which in this instance covers 290-2340 MHz, or approximately 2 GHz in bandwidth. 
       Brief Summary of Embodiments 
       [0006]    According to various embodiments of the disclosed technology systems and methods may be provided in which a low noise block integrated circuit may include a plurality of analog inputs, an analog-to-digital converter and a digital CSS, and a method of operation may include: receiving a first satellite signal centered at a first frequency; receiving a second satellite signal centered at a second frequency; combining the first and second satellite signals to form a combined signal; the analog-to-digital converter transforming the combined signal from an analog signal to a digital signal; and providing the digital signal to the digital CSS. 
         [0007]    In various embodiments, the first and second frequency may be the same frequency or different frequencies. The operation may further include adjusting at least one of the first and second frequencies prior to combining the satellite signals. 
         [0008]    The operation may further include receiving a third satellite signal centered at a third frequency; receiving a fourth satellite signal centered at a fourth frequency; translating the third satellite signal to a fifth frequency, combining the translated third satellite signal with fourth satellite signals to form a second combined signal; a second analog-to-digital converter transforming the combined signal from an analog signal to a second digital signal; and providing the second digital signal to the digital CSS. 
         [0009]    In various embodiments, the third and fourth frequency are the same frequency and translating may include translating the third frequency to a frequency far enough away from the fourth frequency to avoid interference between the translated third satellite signal with the fourth satellite signal upon combining. 
         [0010]    A low noise block may include: a first input signal trace configured to receive a first satellite signal centered at a first frequency; a second signal trace configured to receive a second satellite signal centered at a second frequency; a combiner having a first input connected to the first input signal trace and a second input connected to the second signal trace, and configured to combine the first and second satellite signals to generate and output a combined satellite signal; and an analog-to-digital converter element having a first input coupled to receive the combined satellite signal, and configured to convert the combined satellite signal from an analog signal to a digital signal. 
         [0011]    In various embodiments, the first and second satellite signals are at the same frequency and the LNB further includes a frequency translator, configured to change the frequency of at least one of the first and second satellite signals prior to sending the at least one of the first and second satellite signals to the combiner. The LNB may further include a CSS having an input coupled to receive the digital signal from the analog-to-digital converter. 
         [0012]    In various embodiments, a low noise block circuit may include: a first input signal trace configured to receive a first Ka-band satellite signal centered at a first frequency; a second signal trace configured to receive a first Ku-band satellite signal centered at a second frequency; a combiner having a first input connected to the first input signal trace and a second input connected to the second signal trace, and configured to combine the first Ka-band satellite signal with the first Ku-band satellite signal to generate and output a combined satellite signal; an analog-to-digital converter having a first input coupled to receive the combined satellite signal, and configured to convert the combined satellite signal from an analog signal to a digital signal; a third input signal trace configured to receive a second Ka-band satellite signal centered at the first frequency; a fourth signal trace configured to receive a second Ku-band satellite signal centered at the second frequency; a combiner having a first input connected to the first input signal trace and a second input connected to the second signal trace, and configured to combine the second Ka-band satellite signal with the second Ku-band satellite signal to generate and output a second combined satellite signal; and a second analog-to-digital converter having a first input coupled to receive the second combined satellite signal, and configured to convert the second combined satellite signal from an analog signal to a digital signal. 
         [0013]    The low noise block may further include: a fifth input signal trace configured to receive a third Ka-band satellite signal centered at the first frequency; a sixth signal trace configured to receive a fourth Ka-band satellite signal centered at the first frequency; a frequency translator configured to translate the third Ka-band satellite signal to a different frequency; a third combiner having a first input connected to the an output of the frequency translator and a second input connected to the sixth signal trace, and configured to combine the third Ka-band satellite signal with the translated third Ka-band satellite signal to generate and output a third combined satellite signal; and a third analog-to-digital converter having a first input coupled to receive the third combined satellite signal, and configured to convert the third combined satellite signal from an analog signal to a digital signal. 
         [0014]    In other embodiments, a WiFi front-end module integrated circuit may include plurality of analog inputs, an analog-to-digital converter and a baseband processor, and an operation for implementing a shared ADC, may include: receiving a first WiFi signal centered at a first frequency; receiving a second WiFi signal centered at a second frequency; combining the first and second WiFi signals to form a combined signal; the analog-to-digital converter transforming the combined signal from an analog signal to a digital signal; and providing the digital signal to the digital baseband processor. 
         [0015]    In some embodiments, the first and second frequency are the same frequency, and the operation may further include adjusting at least one of the first and second frequencies prior to combining the WiFi signals. In other embodiments, the first and second frequency are different frequencies. 
         [0016]    In various embodiments, the operation may further include: receiving a third WiFi signal centered at a third frequency; receiving a fourth WiFi signal centered at a fourth frequency; translating the third WiFi signal to a fifth frequency, combining the translated third WiFi signal with fourth WiFi signals to form a second combined signal; a second analog-to-digital converter transforming the combined signal from an analog signal to a second digital signal; and providing the second digital signal to the digital CSS. 
         [0017]    In some embodiments, the third and fourth frequency are the same frequency and translating includes translating the third frequency to a frequency far enough away from the fourth frequency to avoid interference between the translated third WiFi signal with the fourth WiFi signal upon combining. 
         [0018]    A WiFi front-end module may include: a first input signal trace configured to receive a first WiFi signal centered at a first frequency; a second signal trace configured to receive a second WiFi signal centered at a second frequency; a combiner having a first input connected to the first input signal trace and a second input connected to the second signal trace, and configured to combine the first and second WiFi signals to generate and output a combined WiFi signal; and an analog-to-digital converter element having a first input coupled to receive the combined WiFi signal, and configured to convert the combined WiFi signal from an analog signal to a digital signal. 
         [0019]    In some embodiments of a WiFi front-end module the first and second WiFi signals are at the same frequency and further comprising a frequency translator, configured to change the frequency of at least one of the first and second WiFi signals prior to sending the at least one of the first and second WiFi signals to the combiner. 
         [0020]    The WiFi front-end module may further include a baseband processor having an input coupled to receive the digital signal from the analog-to-digital converter. 
         [0021]    Other features and aspects of the disclosed technology will become apparent from the following detailed description, taken in conjunction with the accompanying drawings, which illustrate, by way of example, the features in accordance with embodiments of the disclosed technology. The summary is not intended to limit the scope of any inventions described herein, which are defined solely by the claims attached hereto. 
     
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         [0022]    The technology disclosed herein, in accordance with one or more various embodiments, is described in detail with reference to the following figures. The drawings are provided for purposes of illustration only and merely depict typical or example embodiments of the disclosed technology. These drawings are provided to facilitate the reader&#39;s understanding of the disclosed technology and shall not be considered limiting of the breadth, scope, or applicability thereof. It should be noted that for clarity and ease of illustration these drawings are not necessarily made to scale. 
           [0023]      FIG. 1  is a diagram illustrating a typically outdoor unit. 
           [0024]      FIG. 2  is a diagram illustrating an example implementation of a low noise block. 
           [0025]      FIG. 3  is a diagram illustrating another example of a low noise block (LNB). 
           [0026]      FIG. 4  is a diagram illustrating an example of an LNB in accordance with one embodiment of the technology disclosed herein. 
           [0027]      FIG. 5  is a diagram illustrating another example of an LNB, but configured to handle  3  satellites, each having left and right polarizations. 
           [0028]      FIG. 6 , which comprises  FIGS. 6A and 6B , is a diagram illustrating an example of a shared analog-to-digital converter in accordance with one embodiment of the technology disclosed herein. 
           [0029]      FIG. 7 , which comprises  FIGS. 7A and 7B , is a diagram illustrating an example of implementing a combiner with a shared ADC in an LNB IC. 
           [0030]      FIG. 8  is a block diagram illustrating an example of cross-coupling signal cancellation in accordance with one embodiment of the technology disclosed herein. 
           [0031]      FIG. 9  is a diagram illustrating an example implementation of cross-coupling signal cancellation in accordance with one embodiment of the technology disclosed herein. 
           [0032]      FIG. 10  is a diagram illustrating the details of an example adaptive filter. 
           [0033]      FIG. 11  is an operational flow diagram illustrating an example process for cross-coupling signal cancellation in accordance with one embodiment of the technology disclosed herein. 
           [0034]      FIG. 12  is an operational flow diagram illustrating another example process for cross-coupling signal cancellation in accordance with one embodiment of the technology disclosed herein. 
           [0035]      FIG. 13  is a diagram illustrating an example of three transponders received as part of a satellite signal. 
           [0036]      FIG. 14  is a diagram illustrating an example process for adjusting the oscillator frequency to correct for changes in the center channel frequency in accordance with one embodiment of the technology disclosed herein. 
           [0037]      FIG. 15  is a diagram illustrating an example of a DRO in accordance with one embodiment of the technology disclosed herein. 
           [0038]      FIG. 16  is a diagram illustrating another example of a dielectric resonator oscillator that may be implemented in accordance with various embodiments of the technology disclosed herein. 
           [0039]      FIG. 17  is a diagram illustrating another example of a dielectric resonator oscillator that may be implemented in accordance with various embodiments of the technology disclosed herein. 
           [0040]      FIG. 18  is a diagram illustrating an example implementation of an integrated DRO in accordance with one embodiment of the technology disclosed herein. 
           [0041]      FIG. 19  is another diagram illustrating the inclusion of active elements of the dielectric resonator oscillator on a die and passive elements on the substrate. 
           [0042]      FIG. 20  is a diagram illustrating an example computing module which can be used in accordance with various embodiments of the technology described herein. 
       
    
    
       [0043]    The figures are not intended to be exhaustive or to limit the invention to the precise form disclosed. It should be understood that the invention can be practiced with modification and alteration, and that the disclosed technology be limited only by the claims and the equivalents thereof. 
       DETAILED DESCRIPTION OF THE EMBODIMENTS 
       [0044]    Embodiments of the technology disclosed herein are directed toward a devices and methods for providing techniques for improving satellite communications. More particularly, the various embodiments of the technology disclosed herein relate to improved LNB configurations. 
         [0045]      FIG. 4  is a diagram illustrating an example of an LNB in accordance with one embodiment of the technology disclosed herein. The example illustrated in  FIG. 4  is one of a single satellite implementation with Vertical and Horizontal polarizations. In this example, the satellite signals are Ku band satellite signals however, the LNB can be configured for use with other satellite bands. This example includes a low noise block (LNB) IC  250  that can be implemented, for example, on a single or multiple integrated circuits. LNB IC  250  in this example includes analog variable gain amplifiers  252 , bandpass filters  254 , analog-to-digital converters  255 , a filtering, cross cancellation and matrix switch module  257 , digital-to-analog converters  258 , a control and interface module  259 , a dielectric puck resonator  251 , a local oscillator  253 , and a clock generator  256 . The LNB can also include low noise amplifiers (LNA) and bandpass filters (BPF), which can be implemented, for example, as LNAs  141  and BPFs  142 . 
         [0046]    In operation, the amplitude of the incoming signals is adjusted by variable gain amplifiers  252  and unwanted noise outside of the desired frequency bands is removed by bandpass filters  254 . The analog signal is sampled by analog-to-digital converters  255  using a clock provided by clock generator  256 . The resulting digital signals can be processed by module  257 , which can provide further filtering, cross coupling cancellation, and switching to the designated output or outputs. Digital-to-analog converters  258  convert the outputs to digital form for distribution to the set top boxes. LNB  250  can be configured and implemented to perform what is sometimes referred to as channel stacking (CSS) as described in more detail below. 
         [0047]    Various features of the technology disclosed herein can be implemented for use in this example LNB as well as in other LNB configurations, as will become apparent to one of ordinary skill in the art after reading this description. For example, various features described in terms of this example LNB IC  250  can be implemented with quad, twin, single, and wideband LNB circuits. For a wideband LNB implementation, rather than four outputs at 950-2150 MHz, the LNB can be implemented with two outputs, each at 290-2340 MHz IF each (each 2.05 GHz wide). 
         [0048]    In some embodiments, the dielectric resonator can be implemented in an integrated fashion with the LNB IC. As discussed further below, in some embodiments, the dielectric resonator oscillator, or DRO, can be integrated with the IC package. Consider, for example, the case of a flip chip integrated circuit. In this application, the dielectric puck and associated transmission lines can be mounted on a substrate of the flip chip package all the active components of the DRO can be fabricated as part of the integrated circuit die. Accordingly, the DRO can be configured to consume less real estate, require fewer discrete components (e.g. discrete transistors) and realize a lower production cost. Likewise, the DRO can be implemented to provide a stabilized reference frequency without the need for a PLL. 
         [0049]    Another feature that can be implemented in various embodiments are systems and methods for correcting frequency error in the local oscillator. As described below, embodiments can be implemented to profile the incoming transponders spectral shape, or to identify spectral nulls between transponders to determine and maintain the appropriate center frequency in a closed loop. Embodiments can be implemented such that internal filters and the output frequency are digitally corrected, while other embodiments are configured such that the local oscillator can be physically tuned to the correct center frequencies such as through the use of tuned or switched capacitors. 
         [0050]    Another feature that can be implemented in various embodiments are systems and methods for cross canceling and removing undesired cross coupling of signals that may occur in the IC. In various embodiments, this can be done on a pin for pin basis such that cross coupling can be reduced or eliminated across adjacent pins or across other pin pairs over which cross coupling may occur. Embodiments can be implemented where the correction occurs on an ongoing basis through the use of power measurement and filter coefficient adjustment. The adjustment can continue until the measured power reaches a relative minimum. 
         [0051]    Still another feature that can be implemented in various embodiments is direct on-frequency sampling of the incoming signal at the satellite band, with digital filtering, processing and routing. This can allow, in effect, a direct downconversion and reduce the number of components otherwise required to implement the LNB. 
         [0052]    Yet another feature that can be implemented in various embodiments is that of shared analog-to-digital converters. In various embodiments, signals of different frequencies can be combined and sampled using one analog-to-digital converter as opposed to using multiple analog-to-digital converters. Embodiments can be implemented to reduce the number of components required for the LNB IC. 
         [0053]      FIG. 5  is a diagram illustrating another example of an LNB, this time configured to handle  3  satellites, each having left and right polarizations. As with the example shown in  FIG. 4 , this example includes one or more low noise amplifiers and bandpass filters at the front end of the system. In the case of Ka band, two bandpass filters can be used, one each signal to select the high and low bands of the Ka band. The example of  FIG. 5  also includes an LNB IC  310 . In this example, LNB IC  310  includes variable gain amplifiers  314 , bandpass filters  316 , and analog-to-digital converters  318 , and a digital-to-analog converter  320  at the output. This example also includes a channel stacking switch (CSS)  311 , which can be implemented, for example, part of LNB IC  310 . Additionally, a control and interface module  322  is included to provide control of CSS  311  and other components of the LNB IC  310 . A dielectric puck resonator  324  with the appropriate clock generation circuitry can also be provided. The various features described above that may be included in various embodiments of LNB IC  250  may also be included with LNB IC  310 . 
         [0054]    As noted above, in various embodiments systems and methods can be implemented to provide sharing of analog-to-digital converters (e.g. analog-to-digital converters  318  of  FIG. 5 ) in the LNB. Particularly, embodiments can be implemented in which the signals of different frequencies can be combined together and then sampled using a single ADC. The resultant digital representation of the combined signals can then be provided to the CSS (or other processing module) for further processing and handling.  FIG. 6 , which comprises  FIGS. 6A and 6B , is a diagram illustrating an example of a shared analog-to-digital converter in accordance with one embodiment of the technology disclosed herein. The example of  FIG. 6A  is depicted in terms of two different satellite signals, one at the Ka band and the other at the Ku band. Ka band signals are for example 18.3-18.8 GHz (low band), and 19.7-20.2 GHz (high band), while Ku band signals range from 12.2-12.7 GHz. The example of  FIG. 6B  is depicted in terms of 2 different WiFi signals, one at 2.4 GHz and the other at 5 GHz. After reading this description, one of ordinary skill in the art will appreciate how the shared analog-to-digital converter techniques can be applied with signals at other frequency bands. 
         [0055]    Turning first to  FIG. 6A , for illustration purposes, the system is shown as having two low noise amplifiers  351  and two bandpass filters  352 . These can, for example, represent the low noise amplifiers and bandpass filters depicted in  FIGS. 3 and 4  to the left of the inputs of the LNB ICs.  FIG. 6A  also depicts a portion of an example LNB IC  350  to illustrate an embodiment of the shared analog-to-digital converter. In this example, LNB IC  350  includes two variable gain amplifiers  353 , one for each input signal. LNB IC  350  also includes two bandpass filters  354 , one for each input signal. A combiner  355  is provided to combine the two input signals into a single analog signal. The combining can be, for example, a simple spectral combination of signals. The combiner  355  can be implemented as a combiner, passive diplexer, or other device to mix together the two satellite signals. Preferably, the signals chosen for combination are signals having frequencies that do not overlap with one another such that the combination does not provide unwanted interference. 
         [0056]    Because the signals are combined, they can be digitized for further processing using a single analog-to-digital converter  356 . This is contrasted with conventional solutions in which a separate analog-to-digital converter would have been used for each input signal. The signal combining can be performed on or off chip, but is illustrated on chip in the example of  FIG. 6A . An external frequency conversion can be included to handle situations where incoming signals are at the same frequencies. Accordingly, one (or both) of the signals can be converted to a different frequency so that the frequencies of the two signals are non-overlapping, allowing the combination by the combiner. For example, additional feeds at a given band can be downconverted (e.g. externally) to an intermediate frequency and then combined with another feed from the same band for shared sampling. In some embodiments, the sampling clock frequency for the analog-to-digital conversion is selected in between the Ka and the Ku bands. For example, the sampling clock frequency can be selected at 15.85 GHz. 
         [0057]      FIG. 6B  is a diagram illustrating a similar configuration as in  FIG. 6A , but configured for operating at WiFi frequencies. As illustrated in this example, the system is configured to combine signals at two different WiFi frequencies, 2.4 GHz and 5 GHz, and to digitize the combined signal using a single analog-to-digital converter  356 . Although two specific bands are shown in this example, the shared analog-to-digital converter can be implemented for combined signals from other multiple WiFi bands including, for example, 3.6 GHz, 6 GHz, and so on. 
         [0058]    It is noted that components  352 - 356  are illustrated using the same reference numerals as the Ka/Ku band implementation, to reflect similar functionality. However, as will be apparent to one of ordinary skill in the art after reading this discussion, these components can be selected and tuned to operate at the corresponding WiFi frequencies. For example, for sampling in different Nyquist zones, the sampling clock frequency can be chosen between the 2.4 GHz and 5 GHz bands (e.g. at ˜5 GHz). After sampling, the 2.4 GHz band (which falls into the first Nyquist zone) in the digital domain will remain at 2.4 GHz, while the 5 GHz band (located in the third Nyquist zone) is translated to approximately 0.8 GHz. In another embodiment, the sampling clock frequency can be set at above the 5 GHz band (e.g., at ˜6 GHz), in which case, the 2.4 GHz band remains at 2.4 GHz after sampling, while the 5 GHz (now in the second Nyquist zone) is translated to about 0.2 GHz. Internal bandpass filtering  354  can be provided to suppress aliasing of noise on to the desired signal from other Nyquist zones and between the bands. Preferably, in various embodiments, the filters are centered at the WiFi bands of interest. In other embodiments, the internal bandpass filters  354  may be eliminated to simplify the architecture. 
         [0059]    Although the examples above in  FIGS. 6A and 6B  are illustrated in terms of combining two signals, embodiments can be implemented in which two or more signals are combined. In various embodiments, the signals can be level adjusted using, for example, the variable gain amplifier  353  (e.g. automatic gain control) prior to combining. Signal combination can, for example, be direct wired-OR combining such as by using diplexing filters connected to the same point. In other embodiments, the signal combining can be accomplished using a summing circuit. Clock frequencies for sampling can be chosen in various embodiments to place the multiple bands in different Nyquist zones, while in other embodiments the clock frequency can be chosen to place the bands in a first Nyquist zone. 
         [0060]      FIG. 7 , which comprises  FIGS. 7A and 7B , is a diagram illustrating example implementations of a combiner with a shared ADC. An example of implementing a combiner with the shared ADC in an LNB IC is illustrated in  FIG. 7A , while an example of implementing a combiner with the shared ADC in a WiFi IC is illustrated in  FIG. 7B . Referring now to  FIG. 7A , in this example LNB IC  310  still includes signal inputs for three satellites: two at Ka band and one at the Ku band. Because the Ku band and Ka band satellite signals are at different frequencies, they can be combined without any appreciable interference. Accordingly, one polarization of the Ku band signal is combined with one polarization of the Ka band signal at a first combiner  355 A, and the combined signal is converted by the first analog-to-digital converter  356 A, and the digital signal is provided to the CSS  311 . Similarly, the other polarization of the Ku band signal is combined with the other polarization of the Ka band signal at second combiner  355 B. The combined signal is likewise digitized by analog-to-digital converter  356 B. When compared to the example of  FIG. 5 , the example of  FIG. 7A  includes two fewer analog-to-digital converters while only adding to combiners. 
         [0061]    As noted above, embodiments can be implemented in which a frequency translation is performed to separate two signals in frequency such that they can be combined with a single analog-to-digital converter. Accordingly, in such embodiments, the implementation of  FIG. 7A  could be further modified to adjust the frequency of either or both of the Ka band signals  321 ,  323 , and to combine the adjusted signals using a combiner (e.g. like combiner  355 ) to route the combined signal through a single analog-to-digital converter. For example, in some embodiments, one of the signals can be downconverted to an intermediate frequency prior to being combined. 
         [0062]    Referring now to  FIG. 7B , in this example a WiFi IC  410  includes signal inputs and outputs for two WiFi frequencies. Those are WiFi frequencies of 5 GHz and 2.4 GHz. Because the signals are at different frequencies, they can be combined on the receive side without any appreciable interference. Accordingly when switches  422 ,  423  for each band are set to the receive position, signals from both the 5 GHz and 2.4 GHz antennas are routed through the respective variable gain amplifiers  353  and bandpass filters  354 , and are combined by combiner  355  so that they can be sampled using a single analog-to-digital converter  356 . As noted above, the variable gain amplifiers, bandpass filters, combiners, analog to digital converters and sampling clocks are selected and tuned based on the operating frequencies of the WiFi signals. As this example illustrates, a single analog-to-digital converter can be used to support a multi-band concurrent WiFi architecture. Additionally, greater than two bands can be supported provided the frequencies will not interfere with one another when the signals are combined, or provided that potentially interfering frequencies are translated to a non-interfering frequency prior to combining. Although one antenna for each band is shown in this example, multiple MIMO antennas can be served with a similar architecture repeated for each antenna. For example, in one embodiment, the system can be configured to support a 4×4 MIMO in the 5 GHz band in a 2×2 MIMO in the 2.4 GHz band. As this example serves to illustrate, other MIMO configurations in frequency bands can be supported. 
         [0063]    Another feature that can be included in one or more embodiments is signal cancellation to reduce or eliminate cross coupling effects. With high-frequency signal such as those involved in satellite reception and distribution systems cross coupling can occur between adjacent signals. This can occur at numerous places along the downlink path between the satellites and set-top boxes. One place that such cross coupling may also occur is that the LNB. Particularly, satellite signals on adjacent pins of an LNB IC or otherwise on signal paths close enough to allow cross coupling may experience this effect. Accordingly, techniques can be implemented to reduce or eliminate the effects of cross coupling.  FIG. 8  is a block diagram illustrating an example of cross-coupling signal cancellation in accordance with one embodiment of the technology disclosed herein. Referring now to  FIG. 8 , this example illustrates a portion of an LNB  400  with an LNB IC  410 . LNB IC  410  can be implemented, for example, using an LNB IC such as LNB IC  310  described above. Accordingly, LNB IC  410  includes variable gain amplifiers, bandpass filters and analog-to-digital converters. LNB IC  410  can also include a CSS module (e.g. CSS  311 ) that can further include a module for cross-coupling signal cancellation. 
         [0064]    In various embodiments, the cross-coupling signal cancellation module can be configured to reduce or eliminate cross coupling of the input signals that may occur in the air, in the feed horn, on the printed circuit board, in the power supply, on the IC pins, and so on. This result of this coupling, the signals at d1 and d2 may be cross contaminated in that each signal may contain some energy from the other signal. As a result of cross-coupling signal cancellation module, outputs D1, D2 can be a cleaned-up signal with cross contamination removed or suppressed. 
         [0065]    The cross-coupling signal cancellation can be implemented using knowledge of the interfering signal. Particularly, a first of the two signals can be inverted and combined with a delayed version of the other of the two signals to cancel out (partially or completely) the interfering signal. The amount of delay is chosen such that the inverted signal aligns with the non-inverted version of that signal such that cancellation can occur. In addition, the amplitude of the inverted signal can be adjusted to adjust the level of cancellation. Adaptive filters can be used to make phase and amplitude adjustments at the appropriate frequency or frequencies. 
         [0066]      FIG. 9  is a diagram illustrating an example implementation of cross-coupling signal cancellation in accordance with one embodiment of the technology disclosed herein. Particularly,  FIG. 9  illustrates an example module that can be used to implement cross-coupling signal cancellation module  411  of  FIG. 8 . In this example, the potentially interfering signals are designated by d1 and d2. For ease of discussion, this example will be discussed in terms of d1 being an original signal and d2 being the interfering signal. However, after reading this description, one of ordinary skill in the art will understand that either signal can interfere with the other signal. Referring now to  FIG. 9 , the original signal is received and delayed using delay block  462 . Delay block  462  can be implemented using any of a number of conventional delay techniques including, for example, delay lines or, in digital implementations, by simply storing or holding the signal in a buffer or register. Interfering signal d2 is modified by adaptive filter  463  particularly, adaptive filter  463  inverts the interfering signal to create an inverse of the interfering signal. The phase and amplitude adjustments can be made by changing the tap weights using tap weight vector computation block  468 . Then, the filtered interfering signal is subtracted from the delayed original signal using subtraction block  466 . Alternatively, the interfering signal can also be inverted and added into the original signal to effectively subtract the interfering signal from the original signal. 
         [0067]    For cross coupling of signal d1 onto signal d2, a similar process occurs, but in this instance, signal d1 is filtered using adaptive filter  465 , and original signal d2 is delayed using delay module  464 . 
         [0068]      FIG. 10  is a diagram illustrating the details of one of the adaptive filters  463 ,  465 , for example adaptive filter  463 . The Z −1  term denotes a delay by one clock cycle T. The weight components W 1 , W 2  are stored in corresponding adaptive filters  463 ,  465 . Each TWV component W 1 , W 2  is then provided by the weight setting register  501  to a plurality of weighting circuits  505  in each of the corresponding adaptive filters  463 ,  465 . Each of the weighting circuits  505  adjusts the amount of the signal x(n) at each delay point that is to be summed together in a summing circuit  510  based on the particular value of the TWV components W 1 , W 2  associated with that weighting circuit, or adaptive filter  463 ,  465 . Accordingly, the output signal y(n) is the weighted sum of the various delays of x(n): 
         [0000]        y ( n )=   w     0 *( n ) x ( n )+   w     1 *( n ) x ( n− 1)+ . . . +   w     N-1 *( n ) x ( n−N+ 1); 
         [0000]          W   ( n+ 1)=   W   ( n )+2μ e *( n )   x   ( n );
 
         [0000]    where W(n+1) is the tap-weight vector next value at time n+1, the term μ is the adaptation step size and the e*(n) is the conjugate of the residue error value. 
         [0069]    As noted above, in various embodiments cross coupling cancellation can occur for signals (e.g., signals d1, d2) on adjacent pins of the LNB IC, or for cross coupling occurs in other places up to the CSS. For pin-to-pin cancellation, the cancellation can occur for each adjacent pair of pins carrying satellite signals. In further embodiments, the cancellation can occur for all permutations of pairs of pins carrying satellite signals. In yet another embodiment, the cancellation can be implemented for pairs of pins likely to interfere with one another. To prevent potential instability and oscillatory behavior of multiple loops interfering with each other, when one loop is making adjustments, other loops are “frozen” (kept constant without making changes). After the action of the active loop is completed, another loop becomes active while others are frozen. The process continues until all loops are completed, then the maintenance cycle repeats. An additional benefit of processing one loop at the time is in reduced computational complexity, since a single computational engine can be shared between multiple loops, as opposed to the case of simultaneously processing multiple loops, when multiple computational engines would be required. 
         [0070]      FIG. 11  is an operational flow diagram illustrating an example process for cross-coupling signal cancellation in accordance with one embodiment of the technology disclosed herein. In this example, the success of the cancellation, and hence the adjustment of the filter coefficients, can be made based on a measurement of the total output power. Because the output power of a given signal includes the power of the signal itself as well as the added power contributed by the cross coupled signal, when the output power is minimized (assuming all other factors remain equal, this indicates that the cross coupling is also minimized. Accordingly, an iterative least mean squares process can be implemented to adjust the filter coefficients to achieve a minimum power. This can be done on an ongoing basis, if desired, during operations. 
         [0071]    Referring now to  FIG. 11  at a step  602  the total output power is measured. In one embodiment, as illustrated by operation  604 , the output power can be integrated and measured over a predefined period of time to determine the total output power. This can allow a power to be observed over a longer period of time. 
         [0072]    At operation  604 , the filter coefficients are adjusted for the interfering signal to adjust the phase and amplitude of the interfering signal. For example, in terms of the embodiment illustrated in  FIG. 9 , the filter coefficients of adaptive filter  463  are adjusted. At operation  606 , the filtered interfering signal is combined with the original signal to cancel the cross coupled interference from the original signal. That is, the filtered interfering signal, adjusted in amplitude to approximate the amplitude of the cross coupling interference in the original signal, is subtracted from (or its inverse is added to) the original signal. The power is again measured to determine whether it is minimized. This is illustrated by operations  608  and  610 . The operation continues until the power is minimized. In some embodiments, the operation continues to run in a self-adjusting fashion, maintaining the power at minimum. Where the power is at a minimum, the changes to the filter coefficients will be minimal as well, thereby holding the system approximately in a steady state. 
         [0073]    Interference on a given satellite signal can result not only from cross coupling of one adjacent signal, but can also be affected by another adjacent signal. For example, each pin of an LNB IC generally has two adjacent neighbor pins. Accordingly, it may be desirable to cancel out cross coupling that may result from signals on these two adjacent neighbor pins. Accordingly, in some embodiments, a process similar to that described above with reference to  FIG. 11  can be implemented for the signal on the subject pin and one of its adjacent neighbors. Then, once the cross coupling is minimized (e.g. the output power is minimized) the filter coefficients for the first neighbor pin are held constant and the process is repeated for the original pin and the other nearest neighbor pin. This process can be expanded to account for cross coupling onto a given pin by signals in addition to those of the adjacent pins. For example, the process may consider cross coupling effects on a given pin as a result of signals on a plurality of other pins or signal paths near enough to the subject pin to result in appreciable cross coupling. 
         [0074]    An example of this is illustrated in  FIG. 12 . Referring now to  FIG. 12 , as noted the process focuses on cross coupling between a given pair of pins. This can be, for example, a pair of nearest neighbor pins, or another pair of pins across which cross coupling may occur. Accordingly, any adjustments to filter coefficients for the effects caused by signals on other pins (other than the pair under immediate consideration) are held constant. This is illustrated by operation  652 . As described above with reference to  FIG. 11 , the total output power is measured, and the filter coefficients adjusted for the interfering signal. This is illustrated at operation  654 ,  656 . As also described above with reference to  FIG. 11 , the signals are combined in the power level measured to minimize the power at the output of the subject signal. This is illustrated at operations  657  and  658 . 
         [0075]    Once the cross coupling effect on a signal on a selected pin by a signal on first pin is minimized as described immediately above, the process can be repeated for a second pin. Accordingly, the filter coefficients as determined for the first pin are held constant and the filter coefficients for the second pin are adjusted to minimize the power. This is illustrated at operations  659 ,  660 ,  662 . Where interference on a given pin is only addressed for that caused by two other pins (e.g. the nearest-neighbor pins) the operation may be done. However, in embodiments where interference as a result of signals on a number of different pins is being addressed, the process can repeat for each pair of pins under consideration. This is illustrated by operation  665 . For example, in some embodiments, the operation can be repeated such that p pairs of satellite signals are considered, where p comprises a number of possible pairings of satellite signals in the LNB (or the number of pairings likely to give rise to appreciable interference. For example, where interference is being considered across each possible pairing of pins bearing satellite signals, the operation is performed for p pairs of satellite signals, where p is given by n!/2(n−2), and where n is the number of satellite signals under consideration. 
         [0076]    In various embodiments the amplitude of the cancellation signal is adapted to approximate the amplitude of the cross coupling signal affecting the signal under consideration. In some embodiments, convergence may occur more quickly where the filter coefficients are chosen such that the starting point for the amplitude is estimated as close as possible to the predicted level of interference caused by the cross coupling. Accordingly, parameter such as the distance between signal pairs and the frequency of the interfering signal can be taken into consideration when setting the initial filter coefficients. 
         [0077]    As noted above, in various embodiments another feature that can be included is the ability to correct the frequency of the local oscillator, or ultimately, of the clocks used to sample the analog-to-digital converters. Embodiments of the technology disclosed herein accomplish this, in part, based on knowledge of the transponders received with the satellite signal. Because transponder characteristics such as center frequency and bandwidth are well defined, these characteristics can be used to identify the center frequency using the received signal. Generally speaking, in some embodiments, the system can be configured to receive the satellite signal with a known predefined bandwidth and a center frequency, determine the profile of the satellite signal, and compute the center frequency of the satellite signal based on the profile of the received signal. Once that is accomplished, the system can be configured to generate a reference signal at the computed center frequency. 
         [0078]      FIG. 13  is a diagram illustrating an example of three transponders received as part of a satellite signal. As seen in this example at  13 ( a ), each transponder has a center frequency, f c , and a defined bandwidth  710 . The spacing between the center frequencies of each transponder is known as is the bandwidth. The transponder center frequency is typically very stable, and as such can be used as a reference for the local oscillator frequency. The oscillator may have an inaccurate frequency due to component tolerances, as well as its frequency can drift as a result of temperature variations or instability over time and aging. As a result of the tolerance and drift, local oscillator frequency, f LO , is offset from transponder center frequency, f c , by an unknown amount. Therefore, the known spectral shape of the transponder can be used to identify the center frequency. 
         [0079]      FIG. 14  is a diagram illustrating an example process for adjusting the oscillator frequency to correct for changes in the center channel frequency in accordance with one embodiment of the technology disclosed herein. With reference now to  FIG. 14  at operation  712 , a transponder is selected. At operation  714 , the tuning for that transponder is swept above and below the reference frequency generated directly or indirectly by the oscillator. This is, for example, the estimated center channel frequency for the transponder. A purpose of sweeping above and below the reference frequency is to profile the amplitude response of the transponder. For example, the system can be configured to determine the upper and lower rolloff points of the received transponder signal based on, for example, measured signal strength. Because the center frequency is midway between the upper and lower rolloff points, the center frequency can be determined based on this profiling. This is illustrated by operation  716 . At operation  718 , the oscillator can be tuned to the center frequency, or otherwise adjusted such that derivatives thereof (e.g., generated by frequency multipliers or dividers) will be at or substantially at a center frequency of the transponder. For example, a varactor may be used to tune the oscillator or, capacitors and a bank of capacitors can be switched in or out of the circuit to tune the operating frequency. 
         [0080]    Alternatively, the LO frequency is not tuned to the correct center frequency, rather the frequency error is computed and digitally applied and proportionally corrected in all stages that need to have accurate frequency. For example the output frequency at the output of the DAC is proportionally offset to the correct value, while the DAC clock itself is still uncorrected. Accordingly, in such embodiments, implementations can be accomplished in which no physical tuning elements are needed, and the correction is accomplished computationally. 
         [0081]    Once the center frequency of a given transponder is determined, the center frequencies of the other transponders can be determined based on the known spacing between transponder center frequencies. This is illustrated at operation  720 . Although it may be easier to calculate the center frequencies or other transponders based on known separations, in other embodiments, the process described above for sweeping and profiling transponders can be repeated for each transponder. 
         [0082]    In one embodiment, to avoid transponder ambiguity, the outer transponders (i.e. the first or the last transponder in the band) are chosen for the above calibration process. In another embodiment, when the LO frequency f LO  has an error less than half transponder width, any transponder can be used for calibration. 
         [0083]    In another embodiment, rather than profiling based on rolloff points, the system can be configured to measure the signal strength during the sweeping operation and determine spectral nulls of one or more transponder signals. Once the spectral nulls, or minimum power points in the spectrum, are identified the center frequency can again be determined, for example, as the midpoint between the spectral nulls. 
         [0084]    In various embodiments, centering of the LO frequency for WiFi system may be accomplished in a similar manner as described above for satellite implementations. In the case of WiFi implementations, the channel profiles used for the frequency sweep and analysis are those as specified for WiFi channels as opposed to the satellite transponder profiles. 
         [0085]    Another feature as noted above that can be included in various embodiments of the technology disclosed herein includes a dielectric oscillator to provide the clock frequencies used at least for sampling by the analog-to-digital converters and digital-to-analog converters. The clock can be provided directly by the oscillator or through multiplier or divider circuits to provide the desired clock rate. In some embodiments, the oscillator can be configured as a dielectric resonator oscillator (DRO). A dielectric resonator typically comprises a dielectric material (e.g., ceramic or other dielectric) that relies on a change in permittivity at its surface to confine electromagnetic waves for resonance. That is, standing waves can be created within the dielectric material. In various embodiments, the dielectric resonator is a cylindrical material sometimes referred to as a “puck.” Preferably, the puck has a large dielectric constant and a relatively low dissipation factor. The dimensions of the resonator, or puck, are chosen based on the desired resonant frequency. The dielectric resonator provides frequency stabilization at the resonant frequency and typically allows a high Q. The DRO is achieved by combining resonating elements (L, C or R) coupled to an active device such as, for example, a transistor. The feedback element can be included to reflect the standing wave within the resonating element. 
         [0086]      FIG. 15  is a diagram illustrating an example of a DRO in accordance with one embodiment of the technology disclosed herein. Referring now to  FIG. 15 , this example includes a dielectric resonator  810 , a transmission line  811 , a feedback element  815 , and a matching network  822 . In various embodiments, feedback element  815  and matching network  822  may be referred to as active elements  850 . Active elements  850  may also include transistor  818 . Transistor  818  may include, for example, a Si-bipolar transistor, GaAs FET, or CMOS transistor. 
         [0087]    In operation, a signal is input on transmission line  811 . Transmission line  811  can be, for example, a microstrip transmission line. Transmission line  811  is ideally configured as having a length at a quarter wavelength (or integer multiples thereof) of the desired resonant frequency. Dielectric resonator  810  can, for example, be configured as a dielectric puck made of a dielectric material such as, for example, ceramic, porcelain, glass, plastic, or polymer materials having dielectric properties. Feedback element  815  can be provided to reflect the signal back onto transmission line  811  for resonance. Matching network  822  can be included to match the resonator to the load (represented in this example by resistor RD. 
         [0088]      FIG. 16  is a diagram illustrating another example of a dielectric resonator oscillator that may be implemented in accordance with various embodiments of the technology disclosed herein. In the example illustrated in  FIG. 16 , two transmission lines  811  are provided to form a resonant circuit along with the dielectric resonator  810  and feedback element  813 . In another example, the resistor between the two transmission lines  811  is removed, leaving the lines open-circuited. 
         [0089]      FIG. 17  is a diagram illustrating another example of a dielectric resonator oscillator that may be implemented in accordance with various embodiments of the technology disclosed herein. In this example, the two transmission lines  811  are open, unterminated on the input side. 
         [0090]    In various embodiments, advantages can be obtained where the dielectric resonator oscillator is integrated as part of the IC package. For example, in some embodiments some or all of the active elements can be included in the die of the LNB IC. The passive components (e.g., the dielectric resonator  810  in one or more transmission lines  811 ) may be mounted in close proximity to the die such as on the printed circuit board or, on the substrate of the integrated circuit package where the integrated circuit package is a flip chip package.  FIG. 18  is a diagram illustrating an example implementation of an integrated DRO in accordance with one embodiment of the technology disclosed herein. With reference now to  FIG. 18 , illustrated in this example is the general configuration of a flip chip package  870  including a substrate  865  and a die  860 . As this example illustrates active elements  850  of the DRO can be integrated as part of the die. That is, they can be fabricated along with the other circuitry that makes up the LNB IC. As this example also illustrates, dielectric resonator  810  and one or more transmission lines  811  can be included on the substrate  865  of the LNB IC (e.g., flip chip  870 ). For clarity of illustration, the interconnects between the components mounted on the substrate and active elements  850  are not illustrated in this example. However, the electrical interconnects are schematically represented in  FIGS. 15, 16, and 18 , and given this description, one of ordinary skill in the art will understand how to interconnect one or more transmission lines  811  within input and with active elements  850 . 
         [0091]      FIG. 19  is another diagram illustrating the inclusion of active elements of the dielectric resonator oscillator on a die and passive elements on the substrate. Although not illustrated in  FIG. 19 , in another embodiment dielectric resonator, or puck,  810  can be mounted on the printed circuit board adjacent the semiconductor package. In such an embodiment, the one or more transmission lines  811  would be configured as having sufficient length to run from a position adjacent the dielectric resonator  810  to the substrate of the integrated circuit package. 
         [0092]    As used herein, the term module might describe a given unit of functionality that can be performed in accordance with one or more embodiments of the technology disclosed herein. As used herein, a module might be implemented utilizing any form of hardware, software, or a combination thereof. For example, one or more processors, controllers, ASICs, PLAs, PALs, CPLDs, FPGAs, logical components, software routines or other mechanisms might be implemented to make up a module. In implementation, the various modules described herein might be implemented as discrete modules or the functions and features described can be shared in part or in total among one or more modules. In other words, as would be apparent to one of ordinary skill in the art after reading this description, the various features and functionality described herein may be implemented in any given application and can be implemented in one or more separate or shared modules in various combinations and permutations. Even though various features or elements of functionality may be individually described or claimed as separate modules, one of ordinary skill in the art will understand that these features and functionality can be shared among one or more common software and hardware elements, and such description shall not require or imply that separate hardware or software components are used to implement such features or functionality. 
         [0093]    Where components or modules of the technology are implemented in whole or in part using software, in one embodiment, these software elements can be implemented to operate with a computing or processing module capable of carrying out the functionality described with respect thereto. One such example computing module is shown in  FIG. 20 . Various embodiments are described in terms of this example—computing module  900 . After reading this description, it will become apparent to a person skilled in the relevant art how to implement the technology using other computing modules or architectures. 
         [0094]    Referring now to  FIG. 20 , computing module  900  may represent, for example, computing or processing capabilities found within desktop, laptop and notebook computers; hand-held computing devices (PDA&#39;s, smart phones, cell phones, palmtops, etc.); mainframes, supercomputers, workstations or servers; or any other type of special-purpose or general-purpose computing devices as may be desirable or appropriate for a given application or environment. Computing module  900  might also represent computing capabilities embedded within or otherwise available to a given device. For example, a computing module might be found in other electronic devices such as, for example, digital cameras, navigation systems, cellular telephones, portable computing devices, modems, routers, WAPs, terminals and other electronic devices that might include some form of processing capability. 
         [0095]    Computing module  900  might include, for example, one or more processors, controllers, control modules, or other processing devices, such as a processor  904 . Processor  904  might be implemented using a general-purpose or special-purpose processing engine such as, for example, a microprocessor, controller, or other control logic. In the illustrated example, processor  904  is connected to a bus  902 , although any communication medium can be used to facilitate interaction with other components of computing module  900  or to communicate externally. 
         [0096]    Computing module  900  might also include one or more memory modules, simply referred to herein as main memory  908 . For example, preferably random access memory (RAM) or other dynamic memory, might be used for storing information and instructions to be executed by processor  904 . Main memory  908  might also be used for storing temporary variables or other intermediate information during execution of instructions to be executed by processor  904 . Computing module  900  might likewise include a read only memory (“ROM”) or other static storage device coupled to bus  902  for storing static information and instructions for processor  904 . 
         [0097]    The computing module  900  might also include one or more various forms of information storage mechanism  910 , which might include, for example, a media drive  912  and a storage unit interface  920 . The media drive  912  might include a drive or other mechanism to support fixed or removable storage media  914 . For example, a hard disk drive, a floppy disk drive, a magnetic tape drive, an optical disk drive, a CD or DVD drive (R or RW), or other removable or fixed media drive might be provided. Accordingly, storage media  914  might include, for example, a hard disk, a floppy disk, magnetic tape, cartridge, optical disk, a CD or DVD, or other fixed or removable medium that is read by, written to or accessed by media drive  912 . As these examples illustrate, the storage media  914  can include a computer usable storage medium having stored therein computer software or data. 
         [0098]    In alternative embodiments, information storage mechanism  910  might include other similar instrumentalities for allowing computer programs or other instructions or data to be loaded into computing module  900 . Such instrumentalities might include, for example, a fixed or removable storage unit  922  and a storage unit interface  920 . Examples of such storage units  922  and a storage unit interfaces  920  can include a program cartridge and cartridge interface, a removable memory (for example, a flash memory or other removable memory module) and memory slot, a PCMCIA slot and card, and other fixed or removable storage units  922  and a storage unit interfaces  920  that allow software and data to be transferred from the storage unit  922  to computing module  900 . 
         [0099]    Computing module  900  might also include a communications interface  924 . Communications interface  924  might be used to allow software and data to be transferred between computing module  900  and external devices. Examples of communications interface  924  might include a modem or softmodem, a network interface (such as an Ethernet, network interface card, WiMedia, IEEE 802.XX or other interface), a communications port (such as for example, a USB port, IR port, RS232 port Bluetooth® interface, or other port), or other communications interface. Software and data transferred via communications interface  924  might typically be carried on signals, which can be electronic, electromagnetic (which includes optical) or other signals capable of being exchanged by a given communications interface  924 . These signals might be provided to communications interface  924  via a channel  928 . This channel  928  might carry signals and might be implemented using a wired or wireless communication medium. Some examples of a channel might include a phone line, a cellular link, an RF link, an optical link, a network interface, a local or wide area network, and other wired or wireless communications channels. 
         [0100]    In this document, the terms “computer program medium” and “computer usable medium” are used to generally refer to media such as, for example, memory  908 , storage unit  922 , media  914 , and channel  928 . These and other various forms of computer program media or computer usable media may be involved in carrying one or more sequences of one or more instructions to a processing device for execution. Such instructions embodied on the medium, are generally referred to as “computer program code” or a “computer program product” (which may be grouped in the form of computer programs or other groupings). When executed, such instructions might enable the computing module  900  to perform features or functions of the disclosed technology as discussed herein. 
         [0101]    While various embodiments of the disclosed technology have been described above, it should be understood that they have been presented by way of example only, and not of limitation. Likewise, the various diagrams may depict an example architectural or other configuration for the disclosed technology, which is done to aid in understanding the features and functionality that can be included in the disclosed technology. The disclosed technology is not restricted to the illustrated example architectures or configurations, but the desired features can be implemented using a variety of alternative architectures and configurations. Indeed, it will be apparent to one of skill in the art how alternative functional, logical or physical partitioning and configurations can be implemented to implement the desired features of the technology disclosed herein. Also, a multitude of different constituent module names other than those depicted herein can be applied to the various partitions. Additionally, with regard to flow diagrams, operational descriptions and method claims, the order in which the steps are presented herein shall not mandate that various embodiments be implemented to perform the recited functionality in the same order unless the context dictates otherwise. 
         [0102]    Although the disclosed technology is described above in terms of various exemplary embodiments and implementations, it should be understood that the various features, aspects and functionality described in one or more of the individual embodiments are not limited in their applicability to the particular embodiment with which they are described, but instead can be applied, alone or in various combinations, to one or more of the other embodiments of the disclosed technology, whether or not such embodiments are described and whether or not such features are presented as being a part of a described embodiment. Thus, the breadth and scope of the technology disclosed herein should not be limited by any of the above-described exemplary embodiments. 
         [0103]    Terms and phrases used in this document, and variations thereof, unless otherwise expressly stated, should be construed as open ended as opposed to limiting. As examples of the foregoing: the term “including” should be read as meaning “including, without limitation” or the like; the term “example” is used to provide exemplary instances of the item in discussion, not an exhaustive or limiting list thereof; the terms “a” or “an” should be read as meaning “at least one,” “one or more” or the like; and adjectives such as “conventional,” “traditional,” “normal,” “standard,” “known” and terms of similar meaning should not be construed as limiting the item described to a given time period or to an item available as of a given time, but instead should be read to encompass conventional, traditional, normal, or standard technologies that may be available or known now or at any time in the future. Likewise, where this document refers to technologies that would be apparent or known to one of ordinary skill in the art, such technologies encompass those apparent or known to the skilled artisan now or at any time in the future. 
         [0104]    The presence of broadening words and phrases such as “one or more,” “at least,” “but not limited to” or other like phrases in some instances shall not be read to mean that the narrower case is intended or required in instances where such broadening phrases may be absent. The use of the term “module” does not imply that the components or functionality described or claimed as part of the module are all configured in a common package. Indeed, any or all of the various components of a module, whether control logic or other components, can be combined in a single package or separately maintained and can further be distributed in multiple groupings or packages or across multiple locations. 
         [0105]    Additionally, the various embodiments set forth herein are described in terms of exemplary block diagrams, flow charts and other illustrations. As will become apparent to one of ordinary skill in the art after reading this document, the illustrated embodiments and their various alternatives can be implemented without confinement to the illustrated examples. For example, block diagrams and their accompanying description should not be construed as mandating a particular architecture or configuration.