Abstract:
A programmable active frequency-selective circuit includes a first capacitor having a fixed value and a second capacitor having a value defined by a product of a parameter and a plurality of switchable capacitors, wherein the parameter is defined by a gain, a bandwidth mode, and a process resolution. The parameter may be stored in a form of a look-up table and enables a user or manufacturer to program the gain, select the bandwidth mode and tune the process. The frequency-selective circuit may include a differential input and a differential output having a first feedback path connected across a positive output terminal to a negative input terminal and a second feedback path connected across a negative output terminal and a positive input terminal.

Description:
CROSS-REFERENCES TO RELATED APPLICATIONS 
       [0001]    The present application claims benefit under 35 USC 119(e) of U.S. provisional application No. 61/294,781, filed Jan. 13, 2010, entitled “Area Optimized Analog Filter with Bandwidth Control by a Quantized Scaling Function,” the content of which is incorporated herein by reference in its entirety. 
     
    
     BACKGROUND OF THE INVENTION 
       [0002]    The present invention relates to mixed-signal circuits, and more particularly to programmable active filters that improves the bandwidth resolution, wherein the programmability can be performed either by the user or by the manufacturer by means of a look-up table. 
         [0003]    In mixed-signal circuits, a common requirement is that the bandwidth of an analog frequency-selective filter be programmed to a desired value dependent on several variables, such as bandwidth mode and process correction factor. Furthermore, gain selection may affect time constants requiring a further correction. 
         [0004]    When implementing integrated programmable active filters, processing and temperature variations can cause values of the components to vary, which in turn cause the circuit parameters such as the RC product to vary. One approach may use operational amplifiers having high-precision external resistors and capacitors. Other approach may use an integrated filter having an RC product that can be programmed to compensate for process and temperature variations. 
         [0005]      FIG. 1A  shows a schematic of a low-pass filter  10  whose cut-off frequency f c  is shown as being dependent on the gain, bandwidth and processing parameters.  FIG. 1B  is a conventional implementation of low-pass filter  10 . Low-pass filter  10  includes an operational amplifier (op-amp)  11  having a differential input x(t) and a differential output y(t). Op-amp  11  may be a gain circuit having two inverting feedback paths  12 ,  13 . An inverting output is coupled to a non-inverting input of op-amp  11  via feedback path  12 , and a non-inverting output is coupled to an inverting input of the op-amp via feedback path  13 . In the example shown, the low-pass filter is a differential topology to reject common mode noise. It is appreciated that the filter can be converted to a single-ended topology by connecting either of the signal inputs to ground. In the following, only one feedback path will be described as the other feedback path has a mirror function and does not changed the gain, the bandwidth mode and the process variation. 
         [0006]    Feedback path  12  includes a resistor Rfa that together with input resistor Rp defines the gain of the low-pass filter. Feedback path  12  also include a capacitor C 1 a that together with resistor Rfa defines the 3 dB cut-off frequency (i.e., the bandwidth) of the low-pass filter. By adjusting the value of resistor Rfa and/or capacitor C 1   a,  the bandwidth of the low-pass filter can be controlled or corrected, e.g., to compensate for process and temperature variations or to adapt to application demands. In the example described above, the negative input is assumed to be connected to ground, so that the output y(t) is inverting. Similarly, the low-pass filter  10  can also be described as a single-ended low-pass filter having feedback path  13  interposed between the positive output and the negative input of the operational amplifier  11  and the positive input connected to ground. In this case, the gain of the low-pass filter is defined as the ration of Rfb/Rn and the cut-off frequency is defined as fc=1/(2π*Rfb*C 1 b). 
         [0007]    As shown in  FIG. 1B , low-pass filter  10  can be tuned by using a tunable capacitor arrays and multiple resistors connected in series and/or in parallel. In general, the value of capacitance and resistance per unit area in integrated circuit manufacturing processes is not well controlled, and in order to have an appropriate bandwidth resolution, a large number of capacitors and consequently a large number of control bits are required. The large number of capacitors may require a large layout area and increase the cost of the programmable filters. 
         [0008]    Accordingly, it is desirable to provide a user or manufacturer-programmable capacitor value using a small number of capacitor values and a small number of control bits for use in programmable filters. 
       BRIEF SUMMARY OF THE INVENTION 
       [0009]    A specific embodiment of the present invention provides a programmable active frequency-selective circuit. The programmable active frequency-selective circuit includes a first capacitor having a fixed value and a second capacitor having a value defined by a product of a parameter and a plurality of switchable capacitors, wherein the parameter is defined by a gain, a bandwidth mode, and a process resolution. In an embodiment, the gain may be selected between 0 dB and −3 dB. In another embodiment the bandwidth may be selected between a 6 MHz mode and an 8 MHz mode. In yet another embodiment, the process resolution may be selected in steps of 5% between −5% to +5%. 
         [0010]    The programmable active frequency-selective circuit further includes a first resistor having a fixed first value, a second resistor coupled in series with the first resistor, and a switch coupled across the second resistor, wherein the switch is controlled by the parameter to short-circuit the second resistor to set the gain. The programmable active frequency-selective circuit also includes multiple switches, each of the multiple switches corresponds to one of the plurality of switchable capacitors, and a control port coupled to each of the multiple switches. In addition, the programmable active frequency-selective circuit includes a memory for storing the parameter. 
         [0011]    In another embodiment, a control circuit for selecting a bandwidth, a gain and adjusting a process variation of a resistor-capacitor (RC) filter includes a first resistor having a first value, a second resistor having a second value and being connected in series with the first resistor, and a third resistor having a third value. The control circuit further includes a fixed capacitor and a capacitor array coupled in parallel to the fixed capacitor and coupled in parallel to the third resistor, wherein the capacitor array contains multiple switchable capacitors and wherein the fixed capacitor and the capacitor array have a total capacitive value that defines the bandwidth of the RC filter, and wherein the total capacitive value is defined by a parameter, which, in turn, is defined by the bandwidth, the gain, and the process variation. 
         [0012]    In an embodiment, the first, second, and third values of the respective first, second, and third resistors are fixed. In another embodiment, the second resistor may be shorted using a switch that is controlled by the parameter. 
         [0013]    Although the present invention provides a programmable filter that uses a series resistor to enable a gain setting and a process tuning One of ordinary skill in the art would recognize other variations, modifications, and alternatives. For example, the RC filter can be replaced with a gm-C (transconductance-Capacitor) filter. 
     
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         [0014]    The present invention provides advantages that become obvious to those of ordinary skilled in the art after having read the following detailed description of the embodiments that are illustrated in the various figures, in which: 
           [0015]      FIG. 1A  is a block diagram of a programmable low-pass filter that can be used in embodiments of the present invention; 
           [0016]      FIG. 1B  is a conventional schematic circuit diagram of the programmable low-pass filter of  FIG. 1A ; 
           [0017]      FIG. 1C  is an alternative example schematic circuit diagram of the programmable low-pass filter of  FIG. 1A  according to an embodiment of the present invention; 
           [0018]      FIG. 2  is a simplified block diagram of a programmable filter according to an embodiment of the present invention; 
           [0019]      FIG. 3  is a schematic of an exact scaling of capacitance values for filter tuning according to an embodiment of the present invention; 
           [0020]      FIG. 4  is a capacitor layout  400  of the exact scaling of capacitance values of  FIG. 3 ; 
           [0021]      FIG. 5  is an exemplary schematic of a fixed-plus-binary capacitor array implementation of capacitance values for filter tuning according to an embodiment of the present invention; 
           [0022]      FIG. 6  is a capacitor layout with a quantized scaling scheme for the fixed-plus-binary capacitor array implementation of  FIG. 4 ; 
           [0023]    Table  1  illustrates an exact scaling of capacitance values as a function of bandwidth, gain, and process tuning and required capacitance values according to an embodiment of the present invention; 
           [0024]    Table  2  is a truth table for the exact scaling capacitor selection according to an embodiment of the present invention; 
           [0025]    Table  3  illustrates a derivation of quantizing function and required capacitor sizes according to an embodiment of the present invention; and 
           [0026]    Table  4  is a truth table for the quantized scaling function according to an embodiment of the present invention. 
       
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
       [0027]    In the following description, the circuit paths are described as being single-ended for brevity. Although single-ended operations are possible as described above, the preferred embodiments of the present invention are implemented with circuits operating in a fully differential mode. A differential operational mode provides many advantages over a single-ended operational mode such as larger dynamic range, better total harmonic distortion, higher common mode rejection, and immunity to power supply variations. 
         [0028]    Although the exemplary implementation described above relates to a low-pass RC active filter, one of skilled in the art would appreciated that the implantation could be applied to band-pass and high-pass filters by changing the location of the capacitor in the feedback path. 
         [0029]      FIG. 1C  shows an example schematic diagram of an RC active low-pass filter  100  according to an embodiment of the present invention. This diagram is merely an example, which should not unduly limit the scope of the claims recited herein. One of ordinary skill in the art would recognize other variations, modifications, and alternatives. As shown, low-pass filter  100  includes an operational amplifier (Op-amp) having a positive input terminal and a negative input terminal configured to receive a differential input signal x(t) through the respective input resistors Rp and Rn. It is noted that the disclosure herein may apply to other types of filter topologies and realizations such as Sallen-Key, gm-C. As shown, low-pass filter  100  also includes a feedback path  112  that is coupled between a negative out terminal of the Op-amp and the positive input terminal. Low-pass filter  100  also includes a feedback path  113  that is coupled between a positive out terminal of the Op-amp and the negative input terminal. In an embodiment, feedback path  112  includes a capacitor C 1 a and a resistor Rfa, the capacitor C 1 a and together with the resistor Rfa define the cut-off frequency (i.e., the bandwidth) of the low-pass filter. The ratio of resistor Rfa and resistor Rp determines the gain of the low-pass filter. Similarly, feedback path  113  includes a capacitor C 1   b  and a resistor Rfb, the capacitor C 1   b  and together with the resistor Rfb define the cut-off frequency (i.e., the bandwidth) of the low-pass filter. The ratio of resistor Rfb and resistor Rn determines the gain of the low-pass filter. For the sake of brevity, circuits in the following sections are described using a single-ended operational mode. 
         [0030]      FIG. 2  is a simplified block diagram of a programmable frequency-selective circuit  20  according to an embodiment of the present invention. This diagram is merely an example, which should not unduly limit the scope of the claims recited herein. One of ordinary skill in the art would recognize other variations, modifications, and alternatives. Programmable frequency-selective circuit  20  may include a programmable active filter  21  as shown in  FIG. 1A  having a cut-off frequency that is a function of gain, bandwidth, and process parameters. In an embodiment, programmable active filter  21  may include the configuration of  FIG. 1C . It is appreciated that the present invention is not limited to RC filter. Programmable filter  20  further includes a control port coupled to the programmable RC active filter. In addition, programmable filter  20  may include a memory storing a software program that allows a user to modify the gain, bandwidth and the process resolution. In an embodiment, the memory may include a look-up table that allows the user to vary a bandwidth within a bandwidth range, program a gain in a number of steps in dB, and set a process resolution within a predetermined accuracy range. By way of example, and not limitation, the look-up table may includes RAM, ROM, EEPROM or any other medium that can be used to store desired parameters. In an embodiment, the look-up table can be accessed by a special-purpose or general-purpose computer. 
         [0031]    In some applications, the bandwidth of an RC filter may vary. In an exemplary embodiment, the bandwidth of a RC low-pass filter may be set between two modes, namely 6 MHz for NTSC systems or 8 MHz for Pal/SECAM systems. It is an advantage of the present invention to provide an RC filter having a selectable bandwidth, gain and process tuning 
         [0032]    In the description below, exemplary embodiments assume that the bandwidth of the low-pass filter can be set between a 6 MHz mode and an 8 MHz mode, the gain can be programmed in a 3-dB step, and the process tuning is programmed in three steps having 5% resolution, namely −5%, 0, and +5%. This embodiment is merely an example, which should not unduly limit the scope of the claims recited herein. One of ordinary skill in the art would recognize other variations, modifications, and alternatives. 
         [0033]    One technique leading to such scaling is as follows: 
         [0034]    (i) provide scaled capacitance values of 1.000, and 0.750 to establish the bandwidth modes, 
         [0035]    (ii) for each bandwidth mode, further scale the capacitance by a factor of 1.000, and 0.707 to keep the bandwidth constant over gain programming; and 
         [0036]    (iii) for each band mode and gain step, provide four scaling steps of 0.840, 0.952, 1.000, and 1.053 for process tuning 
         [0037]    One way of adjusting the value of an integrated circuit capacitor is to provide an array in which a main capacitor having a smaller value than the nominal capacitance value and a number of smaller capacitors that are connected in parallel to the main capacitor based on a target capacitor value. This approach may have the significant disadvantage that requires an exact capacitor scaling operation, which add significantly to the cost of the active filter. 
         [0038]    Exact scaling may require an array of irregularly sized capacitors. The lack of regular structure in the capacitor array may result in poorly utilized layout area (white space). This approach is not flexible if the gain steps or bandwidth increments are changed because the layout of the entire cap array is impacted. 
         [0039]      FIG. 3  is a schematic of an exact scaling circuit  300  of capacitance values for filter tuning according to an embodiment of the present invention. Exact scaling circuit  300  includes a capacitor array  310  coupled to a resistor array  320 . In an embodiment, capacitor  310  may correspond to capacitor C 1 a in the feedback path  112  and resistor array  320  may correspond to resistor Rp as shown in  FIG. 1C . Capacitor array  310  includes a capacitor CFIX and  11  capacitors C 0  to C 10 , each of the  11  capacitors is connected in parallel to capacitor CFIX through a respective switch. In the example embodiment, the switch may be a MOS transistor. 
         [0040]    Each MOS transistor is turned on and off by a corresponding control bit (b( 0 ) to b( 10 )). Resistor array  320  includes a resistor R 0  that is connected to a resistor R 1  in series. A transistor S 1  is connected across resistor R 0  to short-circuit resistor RO under a control bit r( 0 ). In an embodiment, the control bits for the capacitor array and the resistor array are generated by control port  22  of  FIG. 2 . 
         [0041]      FIG. 4  is an example capacitor layout  400  of the exact scaling approach of  FIG. 3 . In the example shown, the die area for the capacitor array is 0.052 mm 2 , providing a capacitor density of about 1 fF/μm 2 . 
         [0042]    Table 1 illustrates an exact scaling of capacitance values as a function of bandwidth, gain, and process tuning and required capacitance values of  FIG. 3 . Row  1  shows that a bandwidth of 8 MHz, gain of 0 dB and process tuning of −5% can be obtained when the resistor array has a value of 1000 Ω and the capacitor array has a value of 18.9 pF. That is, the switches (or transistors) of the capacitors C 0  to C 10  and the switch S 1  of resistor RO are all turned off. Row  12  (the last row) shows that a bandwidth of 6 MHz, a gain of −3 dB, a processing tuning of +5% can be obtained when the resistor array has a value of 708 Ω and the capacitor array has a value of 39.34 pF. That is, all switches of the capacitors C 0  to C 10  including switch S 1  of resistor R 0  are turned on. Rows  2  to  11  show various other combinations for the different bandwidths, gains, and process tunings. 
         [0043]    Table  2  is a truth table illustrating an example embodiment using the exact scaling approach of  FIG. 3 . Table  2  provides the programmed switch positions for the combinations of the bandwidth, gain, and process tuning. 
         [0044]    In accordance with one embodiment of the present invention, the total scaled capacitance value can be quantized to a given least significant bit (LSB) size, chosen based on overall precision required. The programmable capacitor C(n) is then implemented as a fixed capacitance value (determined by C min ) and a unit-weighted capacitance array ranging from C min  to C max  in steps of C LSB , as shown in the expression (1) below: 
         [0000]        C ( n )= C   min   +n C   LSB   (1)
 
         [0045]    The selection function can be implemented as a logic function, in a hardware lookup table, or in software as, for example: 
         [0000]        n=Q ( g (GAIN, BW, RCTUNE))  (2)
 
         [0000]    where g(·) defines a mapping from each independent variable to the desired capacitance, and Q(·) is a quantizing function. Digital CMOS fabrication processes facilitate the area-efficient implementation of complex tuning functions. Thus, the quantized scaling approach results in area savings because the complexity is transferred from the capacitor array itself to the selection function. 
         [0046]      FIG. 5  is an exemplary schematic of a fixed-plus-binary capacitor array implementation  500  of capacitance values for filter tuning according to an embodiment of the present invention. Fixed-plus-binary capacitor array implementation  500  includes a capacitor array  510  coupled to a resistor array  520 . In an embodiment, capacitor  510  may correspond to capacitor C 1 a in the feedback path  112  and resistor array  520  may correspond to resistor Rp of  FIG. 1C . Capacitor array  510  includes a capacitor CF 1 X and six capacitors C 0 x, C 0  to C 4 , each of the six capacitors is connected in parallel to capacitor CF 1 X through a respective switch. In an example embodiment, the switches may be a MOS transistor. Each MOS transistor is turned on and off by a corresponding control (bit bx( 0 ), b( 0 ) to b( 4 )). In an embodiment, the value of the switchable capacitor is binary-weighted. In an exemplary embodiment, capacitor C 0 x and C 0  may have an identical value, and capacitor C 1  has a value that is twice the value of C 0 , C 2  has a value that is twice the value of C 1 , C 3  has a value that is twice the value of C 2 , and C 3  has a value that is twice the value of C 3 . 
         [0047]    Resistor array  520  includes a resistor R 0  that is connected to a resistor R 1  in series. A transistor S 1  is connected across resistor R 0  to short-circuit resistor RO under a control bit r( 0 ). 
         [0048]    In an embodiment, the control bits for the capacitor array and the resistor array are generated by control port  22  of  FIG. 2 . 
         [0049]    In an exemplary embodiment, an 18.9-pF fixed capacitor is used with a 5-bit capacitor array having a 639-fF LSB. The fixed capacitor is defined by the minimum capacitance required for all inputs. The number of bits and LSB size is then determined by the required precision and span. 
         [0050]    Table  3  shows the derivation of the quantized scaling function of  FIG. 5  according to an embodiment of the present invention. Row  1  shows that a bandwidth of 8 MHz, a gain of 0 dB and a process tuning of −5% can be obtained when the resistor array has a value of 1000 Ω and the capacitor array has a value of 18.9 pF. That is, the switches (or transistors) of the capacitors C 0 x, C 0  to C 4  and the switch S 1  of resistor RO are all turned off. Row  12  (the last row) shows that a bandwidth of 6 MHz, a gain of −3 dB, a processing tuning of +5% can be obtained when the resistor array has a value of 708 Ω and the capacitor array has a value of 39.34 pF. That is, all switches of the capacitors C 0 x, C 0  to C 4  and switch S 1  of resistor R 0  are turned on. Rows  2  to  11  show other combinations for various bandwidths, gains, and process tunings. 
         [0051]    Table  4  is a truth table  400  illustrating an example embodiment using the fixed-plus-binary array approach according to an embodiment of the present invention. Table  4  provides the programmed switch positions for the various combinations of the bandwidth, gain, and process tunings 
         [0052]      FIG. 6  is an example capacitor layout  600  of the fixed-plus-binary array approach of  FIG. 5 . In the example shown, the die area for the capacitor array is 0.047 mm 2 , resulting in a area savings of about 10 percent comparing with the exact scaling approach of  FIG. 3 . The use of a fixed capacitor combined with a binary-weighted capacitor array enables a regular and hence more efficient layout. Although the regular layout using the fixed-plus-binary array approach results in a quantization error of the capacitor step of −1.4% (see last column of Table  3 ), the approach is still advantageous because the process tuning only has a resolution of 5%. Furthermore, the regular array allows a common centroid layout for the capacitor array, and all elements can be designed to have the same perimeter-to-area for better matching. 
         [0053]    Although the exemplary implementation described above relates to a low-pass RC active filter, one of skilled in the art would appreciated that the implantation could be applied to band-pass and high-pass filters by changing the location of the capacitor in the feedback path. 
         [0054]    Embodiments of the present invention are described using a single-ended operational mode. Preferred embodiments of the present invention include differential operational amplifiers and perform differential operations. 
         [0055]    Many alternatives, modifications, and variations will be apparent to those skilled in the art in light of the above teachings. For example, the filter according to embodiments of the present invention may allow the bandwidth selection characteristics to be changed in the following manner as necessary. For example, the resistor Rfa (Rfb) in the feedback path  112  ( 113 ) of  FIG. 1C  may also be made programmable. 
         [0056]    It is understood that the above embodiments of the present invention are illustrative and not limiting. Various alternatives and equivalents are possible. For example, the invention may be applied to other active filter topology such as Sallen-Key, gm-C. The invention is also not limited by the type of integrated circuits in which the present disclosure may be disposed. Other additions, subtractions or modifications are obvious in view of the present invention and are intended to fall within the scope of the appended claims.