Abstract:
In a hold type image display apparatus, a panel includes a plurality of data lines, a plurality of gate lines, and first and second type pixels located at intersections between the data lines and the gate lines. Every one or more of the first type pixels and every one or more of the second type pixels are staggered at the intersections, wherein each of the first type pixels is connected to one of the data lines and two successive ones of the gate lines, and each of the second type pixels is connected to one of the data lines and one of the gate lines. A gate line driver circuit scans two first successive ones of the gate lines for writing first video data and two second successive ones of the gate lines for writing first black data in a first selection period and scans a preceding one of the first successive gate lines for writing second video data and a preceding one of the second successive gate lines for writing second black data in a second selection period. A data line driver circuit supplies the first video data and the first black data to the data lines in the first selection period, and supplies the second video data and the second black data to the data lines in the second selection period.

Description:
BACKGROUND OF THE INVENTION 
     1. Field of the Invention 
     The present invention relates to a hold type image display apparatus such as a liquid crystal display (LCD) apparatus and an electroluminescence (EL) display apparatus and its driving method. 
     2. Description of the Related Art 
     Generally, a hold type image display apparatus such as an LCD apparatus or an EL display apparatus is constructed by a plurality of data lines (or signal lines) driven by a data line driver circuit, a plurality of gate lines (or scan lines) driven by a gate line driver circuit, and pixels each located at one intersection between the data lines and the gate lines. In such a hold type image display apparatus, the quality of display deteriorates due to the residual image phenomenon caused by the low response speed and the hold operation. This will be explained later in detail. 
     In order to suppress the residual image phenomenon, a prior art hold type image display apparatus is suggested to supply video data to pixels on one gate line while supplying black data to pixels on another gate line (see: JP-A-2000-122596). This also will be explained later in detail. 
     In the above-described prior art hold type image display apparatus, however, the data line driver circuit is still large in scale and power consumption. 
     SUMMARY OF THE INVENTION 
     It is an object of the present invention to provide a hold type image display apparatus capable of suppressing the residual image phenomenon while reducing the scale and power consumption of a data line driver circuit. 
     Another object is to provide a panel, a gate line driver circuit and a data line driver circuit used in such a hold type image display apparatus. 
     A further object is to provide a driving method for driving such a hold type image display apparatus. 
     According to the present invention, in a hold type image display apparatus, a panel includes a plurality of data lines, a plurality of gate lines, and first and second type pixels located at intersections between the data lines and the gate lines. Every one or more of the first type pixels and every one or more of the second type pixels are staggered at the intersections, wherein each of the first type pixels is connected to one of the data lines and two successive ones of the gate lines, and each of the second type pixels is connected to one of the data lines and one of the gate lines. A gate line driver circuit scans two first successive ones of the gate lines for writing first video data and two second successive ones of the gate lines for writing first black data in a first selection period and scans a preceding one of the first successive gate lines for writing second video data and a preceding one of the second successive gate lines for writing second black data in a second selection period. A data line driver circuit supplies the first video data and the first black data to the data lines in the first selection period, and supplies the second video data and the second black data to the data lines in the second selection period. 
     Also, the data line driver circuit is constructed by a shift register circuit for receiving two horizontal start pulse signals per one horizontal period to shift the two horizontal start pulse signals in synchronization with a horizontal clock signal; a data register circuit for latching the first and second video data in synchronization with the latch signals; a digital/analog conversion circuit for performing digital/analog conversions upon the first and second video data latched in the data register circuit; a black data voltage generation circuit for generating at least one black data; and an output buffer circuit for multiplexing and supplying the first and second video data and the black data to the data lines. In this case, the shift register circuit includes serially-connected third flip-flops clocked by the horizontal clock signal to generate latch signals, the number of the third flip-flops being half of the number of the data lines. 
     Further, in a method for driving a hold type image display apparatus comprising a panel including a plurality of data lines, a plurality of gate lines, and first and second type pixels located at intersections between the data lines and the gate lines, every one or more of the first type pixels and every one or more of the second type pixels being staggered at the intersections, wherein each of the first type pixels is connected to one of the data lines and two successive ones of the gate lines, and each of the second type pixels is connected to one of the data lines and one of the gate lines, in a first selection period, two first successive ones of the gate lines for writing first video data and two second successive ones of the gate lines for writing first black data are scanned, and the first video data and the first black data are supplied to the data lines. Also, in a second selection period, a preceding one of the first successive gate lines for writing second video data and a preceding one of the second successive gate lines for writing second black data are scanned, and the second video data and the second black data are supplied to the data lines. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       The present invention will be more clearly understood from the description set forth below, as compared with the prior art, with reference to the accompanying drawings, wherein: 
         FIG. 1  is a block circuit diagram illustrating a first prior art LCD apparatus; 
         FIG. 2  is a detailed circuit diagram of the data line driver circuit of  FIG. 1 ; 
         FIG. 3  is a timing diagram for explaining the operation of the data line driver circuit of  FIG. 2 ; 
         FIG. 4  is a detailed circuit diagram of the gate line driver circuit of  FIG. 1 ; 
         FIG. 5  is a timing diagram for explaining the operation of the gate line driver circuit of  FIG. 4 ; 
         FIG. 6  is a timing diagram for explaining the operation of the LCD apparatus of  FIG. 1 ; 
         FIG. 7  is a timing diagram for supplementally explaining the operation of  FIG. 6 ; 
         FIG. 8  is a timing diagram for explaining a cause of the residual image phenomenon in the LCD apparatus of  FIG. 1 ; 
         FIGS. 9A and 9B  are timing diagrams for explaining another cause of the residual image phenomenon in the LCD apparatus of  FIG. 1 ; 
         FIG. 10  is a block circuit diagram illustrating a second prior art LCD apparatus; 
         FIG. 11  is a detailed circuit diagram of the gate line driver circuit of  FIG. 10 ; 
         FIG. 12  is a timing diagram for explaining the operation of the gate line driver circuit of  FIG. 11 ; 
         FIG. 13  is a timing diagram for explaining the operation of the LCD apparatus of  FIG. 10 ; 
         FIG. 14  is a timing diagram for supplementally explaining the operation of  FIG. 13 ; 
         FIG. 15  is a diagram illustrating a black region of the LCD panel of  FIG. 10 ; 
         FIG. 16  is a block circuit diagram illustrating a first embodiment of the LCD apparatus according to the present invention; 
         FIG. 17  is a detailed circuit diagram of the data line driver circuit of  FIG. 16 ; 
         FIG. 18  is a timing diagram for explaining the operation of the data line driver circuit of  FIG. 17 ; 
         FIG. 19  is a detailed circuit diagram of the gate line driver circuit of  FIG. 16 ; 
         FIG. 20  is a timing diagram for explaining the operation of the gate line driver circuit of  FIG. 19 ; 
         FIG. 21  is a timing diagram for explaining the operation of the LCD apparatus of  FIG. 16 ; 
         FIG. 22  is a timing diagram for supplementally explaining the operation of  FIG. 21 ; 
         FIG. 23  is a block circuit diagram illustrating a second embodiment of the LCD apparatus according to the present invention; 
         FIG. 24  is a detailed circuit diagram of the data line driver circuit of  FIG. 23 ; 
         FIG. 25  is a timing diagram for explaining the operation of the data line driver circuit of  FIG. 24 ; 
         FIG. 26  is a timing diagram for explaining the operation of the LCD apparatus of  FIG. 23 ; and 
         FIG. 27  is a timing diagram for supplementally explaining the operation of  FIG. 26 . 
     
    
    
     DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     Before the description of the preferred embodiments, prior art LCD apparatuses will be explained with reference to  FIGS. 1 ,  2 ,  3 ,  4 ,  5 ,  6 ,  7 ,  8 ,  9 A,  9 B,  10 ,  11 ,  12 ,  13 ,  14  and  15 . 
     In  FIG. 1 , which illustrates a first prior art LCD apparatus, reference numeral  11  designates an LCD panel having m×n dots where m is 640 and n is 480, for example. That is, the LCD panel  11  includes m data lines DL 1 , DL 2 , DL 3 , DL 4 , . . . , DL m−1 , DL m  driven by a data line driver circuit  12 , n gate lines GL 1 , GL 2 , GL 3 , GL 4 , . . . , GL n−1 , GL n  driven by a gate line driver circuit  13 , and m×n pixels P ij  (i=1, 2, 3, 4, . . . , m−1, m; j=1, 2, 3, 4, . . . , n−1, n) each located at one intersection between the data lines DL 1 , DL 2 , DL 3 , DL 4 , . . . , DL m−1 , DL m  and the gate lines GL 1 , GL 2 , GL 3 , GL 4 , . . . , GL n−1 , GL n . Each of the pixels P ij  is constructed by one thin film transistor (TFT) Q ij  such as Q 11 , one pixel capacitor C ij  such as C 11  including liquid crystal connected between the TFT Q ij  and a common electrode to which a common voltage VCOM is applied. 
     In  FIG. 2 , which illustrates a detailed circuit diagram of the data line driver circuit  12  of  FIG. 1 , the data line driver circuit  12  is constructed by a shift register circuit  121 , a data register circuit  122 , a data latch circuit  123 , a digital/analog (D/A) conversion circuit  124 , and an output buffer circuit  125 . 
     The shift register circuit  121  shifts a horizontal start pulse signal (HST) as shown in  FIG. 3  in synchronization with a horizontal clock signal HCK as shown in  FIG. 3 . The shift register circuit  121  is formed by serially-connected D-type flip-flops  1211 ,  1212 ,  1213 ,  1214 , . . . ,  121   m −1,  121   m  clocked by rising edges of the horizontal clock signal HCK to generate latch signals LA 1 , LA 2 , LA 3 , LA 4 , , LAm−1, LAm, sequentially, as shown in  FIG. 3 . Note that the horizontal start pulse signal HST is generated from a horizontal timing generating circuit (not shown) which receives a horizontal synchronization signal HSYNC. Also, the horizontal clock signal HCK is generated from a clock signal generating circuit (not shown). 
     The data register circuit  122  latches an 8-bit gradation video data signal VD represented by B 0 , B 1 , . . . , B 7  in accordance with the latch signals LA 1 , LA 2 , LA 3 , LA 4 , . . . , LAm−1, LAm. The data register circuit  122  is formed by 8 D-type flip-flops  1221  clocked by the latch signal LA 1  to latch digital video data D 1  of the gradation video signal VD as shown in  FIG. 3 , 8 D-type flip-flops  1222  clocked by the latch signal LA 2  to latch digital video data D 2  of the gradation video signal VD as shown in  FIG. 3 , 8 D-type flip-flops  1223  clocked by the latch signal LA 3  to latch digital video data D 3  of the gradation video signal VD as shown in  FIG. 3 , 8 D-type flip-flops  1224  clocked by the latch signal LA 4  to latch digital video data D 4  of the gradation video signal VD as shown in  FIG. 3 , 8 D-type flip-flops  122   m− 1clocked by the latch signal LAm−1to latch digital video data Dm−1of the gradation video signal VD as shown in  FIG. 3 , and 8 D-type flip-flops  122   m  clocked by the latch signal LAm to latch digital video data Dm of the gradation video signal VD as shown in  FIG. 3 . In this case, the digital video data D 1 , D 2 , D 3 , D 4 , . . . , Dm−1, Dm of the 8-bit gradation video signal VD are sequentially generated from a signal processing circuit (not shown). 
     The data latch circuit  123  latches and multiplexes the digital video data D 1 , D 2 , D 3 , D 4 , . . . , Dm−1, Dm. The data latch circuit  123  is formed by latch circuits  1231 ,  1232 ,  1233 ,  1234 , ,  123   m− 1,  123   m  clocked by a horizontal strobe signal HSTB as shown in  FIG. 3  which is generated from the horizontal timing generating circuit, and multiplexers  1231 ′,  1232 ′, . . . ,  123   m/ 2′ clocked by a polarity signal POL as shown in  FIG. 3  which is also generated from the horizontal timing generating circuit. This polarity signal POL is used for carrying out a dot inversion method which is advantageous in power consumption. 
     The D/A conversion circuit  124  is formed by positive-side D/A converters  1241 ,  1243 , . . . ,  124   m− 1 for generating analog gradation voltages on the positive side with respect to the common voltage VCOM and negative-side D/A converters  1242 ,  1244 , . . . ,  124   m  for generating analog gradation voltages on the negative side with respect to the common voltage VCOM. That is, if POL=“1”, the latch circuits  1231 ,  1232 ,  1233 ,  1234 , ,  123   m− 1,  123   m  are connected by the multiplexers  1231 ′,  1232 ′, . . . ,  123   m/ 2′ to the D/A converters  1241 ,  1242 ,  1243 ,  1244 , . . . ,  124   m− 1,  124   m , respectively. As a result, the D/A converters  1241 ,  1242 ,  1243 ,  1244 , . . . ,  124   m− 1,  124   m  generate analog video signals corresponding to the digital video signals D 1 , D 2 , D 3 , D 4 , . . . , Dm−1, Dm, respectively. On the other hand, if POL=“0”, the latch circuits  1231 ,  1232 ,  1233 ,  1234 , . . . ,  123   m− 1,  123   m  are connected by the multiplexers  1231 ′,  1232 ′, . . . ,  123   m/ 2′ to the D/A converters  1242 ,  1241 ,  1244 ,  1243 , . . . ,  124   m ,  124   m− 1, respectively. As a result, the D/A converters  1241 ,  1242 ,  1243 ,  1244 , . . . ,  124   m− 1,  124   m  generate analog video signals corresponding to the digital video signals D 2 , D 1 , D 4 , D 3 , . . . , Dm, Dm−1, respectively. 
     The output buffer circuit  125  multiplexes the analog video signals from the D/A conversion circuit  124  in accordance with a data selection signal DSL as shown in  FIG. 3  similar to the polarity signal POL. The data selection signal DSL is generated from the horizontal timing generating circuit. The output buffer circuit  125  is formed by amplifiers (usually, voltage-follower-type operational amplifiers)  1251 ,  1252 ,  1253 ,  1254 , . . . ,  125   m− 1,  125   m  for amplifying the analog video signals from the D/A converters  1241 ,  1242 ,  1243 ,  1244 , . . . ,  124   m− 1,  124   m , respectively, and multiplexers  1251 ′,  1252 ′, . . . ,  125   m/ 2′ clocked by the data selection signal DOL. In this case, the multiplexers  1251 ′,  1252 ′, . . . ,  125   m/ 2′ operate in the same way as the multiplexers  1231 ′,  1232 ′, . . . ,  123   m/ 2′, respectively, of the data latch circuit  123 . That is, if DSL=“1”, the multiplexers  1251 ′,  1252 ′, . . . ,  125   m/ 2′ are in a through state, while if DSL=“0”, the multiplexers  1251 ′,  1252 ′, . . . ,  125   m/ 2′ are in a cross state. Therefore, the analog video signals corresponding to the digital video signals D 1 , D 2 , D 3 , D 4 , . . . , Dm−1, Dm are supplied to the data lines DL 1 , DL 2 , DL 3 , DL 4 , . . . , DL m−1 , DL m , respectively. Note that the analog video signals corresponding to the digital video signals D 2 , D 1 , D 4 , D 3 , . . . , Dm, Dm−1 are never supplied to the respective data lines DL 1 , DL 2 , DL 3 , DL 4 , . . . , DL m−1 , DL m . 
     In  FIG. 4 , which illustrates a detailed circuit diagram of the gate line driver circuit  13  of  FIG. 1 , the gate line driver circuit  13  is constructed by a shift register circuit  131  for shifting a vertical start pulse signal VST as shown in  FIG. 5  in synchronization with a vertical clock signal VCK as shown in  FIG. 5 , and an output buffer circuit  132  formed by amplifiers (usually, voltage-follower-type operational amplifiers)  1321 ,  1322 ,  1323 ,  1324 , . . . ,  132   n− 1,  132   n . Note that one vertical start pulse signal VST is generated per one frame period. This shift register circuit  131  is formed by serially-connected D-type flip-flops  1311 ,  1312 ,  1313 ,  1314 , . . . ,  131   n− 1,  131   n  clocked by rising edges of the vertical clock signal VCK to generate gate line signals (or scan line signals) as shown in  FIG. 5  on the gate lines GL 1 , GL 2 , GL 3 , GL 4 , . . . , GL n−1 , GL n , respectively. 
     As illustrated in  FIG. 6 , in a first frame period T 1 , when video data {circle around (1)}+, {circle around (2)}−, {circle around (3)}+ and {circle around (4)}− are supplied to the data lines DL 1 , DL 2 , DL 3  and DL 4 , respectively, while the gate line signal at the gate line GL 1  is high, the video data {circle around (1)}+, {circle around (2)}−, {circle around (3)}+ and {circle around (4)}− are written into pixels A, B, C and D, respectively, at time t 1  as illustrated in  FIG. 7 . 
     Next, in a second frame period T 2 , when video data {circle around (1)}′−, {circle around (2)}′+, {circle around (3)}′− and {circle around (4)}′+ are supplied to the data lines DL 1 , DL 2 , DL 3  and DL 4 , respectively, while the gate line signal at the gate line GL 2  is high, the video data {circle around (1)}′−, {circle around (2)}′+, {circle around (3)}′− and {circle around (4)}′+ are written into pixels E, F, G and H, respectively, at time t 2  as illustrated in  FIG. 7 . 
     Next, in a third frame period T 3 , when video data {circle around (1)}″+, {circle around (2)}″−, {circle around (3)}″+ and {circle around (4)}″− are supplied to the data lines DL 1 , DL 2 , DL 3  and DL 4 , respectively, while the gate line signal at the gate line GL 3  is high, the video data {circle around (1)}″+, {circle around (2)}″−, {circle around (3)}″+ and {circle around (4)}″− are written into pixels I, J, K and L, respectively, at time t 3  as illustrated in  FIG. 7 . 
     Thereafter, similar operations follow. 
     In the LCD apparatus of  FIG. 1 , however, the quality of display deteriorates due to the residual image phenomenon. For example, if the LCD apparatus of  FIG. 1  is of a twisted nematic (TN) type, the response speed is on the order of 10 ms which is longer than one frame period such as 1/60 sec. As a result, as illustrated in  FIG. 8 , the application of a displayed pixel gradation voltage (brightness) actually cannot follow the writing of its corresponding video data to one of the data lines DL 1 , DL 2 , DL 3 , DL 4 , . . . , DL m−1 , DL m . For example, it will take three or four frame periods for the actual displayed pixel gradation voltage to reach its target voltage represented by the corresponding video data. Thus, the above-mentioned residual image phenomenon is caused by the low response speed of the LCD apparatus of  FIG. 1 . Additionally, the above-mentioned residual image phenomenon is caused, since the LCD apparatus of  FIG. 1  is of a hold type (see: Taiichiro Kurita, “Degradation of Quality of Moving Images Displayed on Hold Type Displays and Its Improving Method”, 1999 Symposium of IEICE, SC-8-1, pp. 207-208, 1999). That is, as illustrated in  FIG. 9A , in a hold type display apparatus such as the LCD apparatus of  FIG. 1 , since a supplied video data gradation holds for one frame period, the supplied video data remains until the next video data is supplied, which would enhance the residual image phenomenon. On the other hand, as illustrated in  FIG. 9B , in an impulse type display apparatus such as a cathode ray tube (CRT) display apparatus, a supplied video data gradation holds only for a short time such as several milliseconds, which would suppress the residual image phenomenon. 
     In  FIG. 10 , which illustrates a second prior art LCD apparatus (see: JP-A-2000-122596), in order to suppress the residual image phenomenon, while video data are supplied to pixels on one gate line, black signals are supplied to pixels on another gate line. 
     In  FIG. 10 , an LCD panel  21 , a data line driver circuit  22  and a gate line driver circuit  23  are provided. In this case, the LCD panel  21  and the data line driver circuit  22  have the same configuration as the LCD panel  11  and the data line driver circuit  12 , respectively, of  FIG. 1 . 
     In  FIG. 11 , which illustrates a detailed circuit diagram of the gate line driver circuit  23  of  FIG. 10 , the gate line driver circuit  23  is constructed by shift register circuits  231  and  232  for shifting a vertical start pulse signal VST as shown in  FIG. 12  in synchronization with a vertical clock signal VCK as shown in  FIG. 12 , a gate circuit  233 , and an output buffer circuit  234  formed by amplifiers (usually, voltage-follower-type operational amplifiers)  2341 ,  2342 ,  2343 ,  2344 , . . . ,  234   n− 1,  234   n.    
     The shift register circuit  231  is formed by serially-connected D-type flip-flops  2311 ,  2312 ,  2313 ,  2314 , . . . ,  231   n− 1,  231   n  clocked by rising edges of the vertical clock signal VCK to generate signals S 1 , S 2 , S 3 , S 4 , . . . , S n−1 , S n  as shown in  FIG. 12 . 
     The shift register circuit  232  is formed by serially-connected D-type flip-flops  2321 ,  2322 ,  2323 ,  2324 , . . . ,  232   n− 1,  232   n  clocked by falling edges of the vertical clock signal VCK to generate signals S 1 ′, S 2 ′, S 3 ′, S 4 ′, . . . , S n−1 ′, S n ′ as shown in  FIG. 12 . 
     The gate circuit  233  is formed by a gate  2331  for receiving the signals S 1  and S 1 ′, a gate  2332  for receiving the signals S 2  and S 2 ′, a gate  2333  for receiving the signals S 3  and S 3 ′, a gate  2334  for receiving the signals S 4  and S 4 ″, . . . , a gate  233   n− 1 for receiving the signals S n−1 , and S n−1 ′, a gate  233   n  for receiving the signals S n  and S n ′, to generate gate line signals (or scan line signals) on the gate lines GL 1 , GL 2 , GL 3 , GL 4 , . . . , GL n−1 , GL n , respectively, as shown in  FIG. 12 . 
     In  FIG. 12 , two vertical start pulse signals VST are generated per one frame period. A first one of the vertical start pulse signals VST is used for writing black data, while a second one of the vertical start pulse signals VST is used for writing video data. 
     As illustrated in  FIG. 13 , in the former half T 1  of a first frame period, when video data {circle around (1)}+, {circle around (2)}−, {circle around (3)}+ and {circle around (4)}− are supplied to the data lines DL 1 , DL 2 , DL 3  and DL 4 , respectively, while the gate line signal at the gate line GL 1  is high, the video data {circle around (1)}+, {circle around (2)}−, {circle around (3)}+ and {circle around (4)}− are written into pixels A, B, C and D, respectively, at time t 1  as illustrated in  FIG. 14 . Subsequently, as illustrated in  FIG. 13 , in the latter half T 1 ′ of the first frame period, when black data B+, B−, B+and B− are supplied to the data lines DL K+1 , DL K+2 , DL K+3  and DL K+4 , respectively, while the gate line signal at the gate line GL K+1  is high, the black data B+, B−, B+ and B− are written into pixels BA, BB, BC and BD, respectively, at time t 1 ′ as illustrated in  FIG. 14 . 
     Next, in the former half T 2  of a second frame period, when video data {circle around (1)}′−, {circle around (2)}′+, {circle around (3)}′− and {circle around (4)}′+ are supplied to the data lines DL 1 , DL 2 , DL 3  and DL 4 , respectively, while the gate line signal at the gate line GL 2  is high, the video data {circle around (1)}′−, {circle around (2)}′+, {circle around (3)}′− and {circle around (4)}′+ are written into pixels E, F, G and H, respectively, at time t 2  as illustrated in  FIG. 14 . Subsequently, in the latter half T 2 ′ of the second frame period, when black data B−, B+, B− and B+ are supplied to the data lines DL 1 , DL 2 , DL 3  and DL 4 , respectively, while the gate line signal at the gate line GL k+2  is high, the black data B−, B+, B− and B+ are written into pixels BE, BF, BG and BH, respectively, at time t 2  as illustrated in  FIG. 14 . 
     Next, in the former half T 3  of a third frame period, when video data {circle around (1)}″+, {circle around (2)}″−, {circle around (3)}″+ and {circle around (4)}″− are supplied to the data lines DL 1 , DL 2 , DL 3  and DL 4 , respectively, while the gate line signal at the gate line GL 3  is high, the video data {circle around (1)}″+, {circle around (2)}″−, {circle around (3)}″+ and {circle around (4)}″− are written into pixels I, J, K and L, respectively, at time t 3  as illustrated in  FIG. 14 . Subsequently, in the latter half T 3 ′ of the third frame period, when video data B+, B−, B+ and B− and supplied to the data lines DL 1 , DL 2 , DL 3  and DL 4 , respectively, while the gate line signal at the gate line GL k+3  is high, the video data B+, B−, B+ and B− are written into pixels BI, BJ, BK and BL, respectively, at time t 3 ′ as illustrated in  FIG. 14 . 
     Thereafter, the same operation as described above is repeated. 
     Thus, as illustrated in  FIG. 15 , a black region having a width of k gate lines where k=1, 2, 3, . . . is scanned on a screen to suppress the residual image phenomenon. 
     In the LCD apparatus of  FIG. 10 , however, since the data line driver circuit  22  has the same configuration as the data driver circuit  12  of  FIG. 2 , the data line driver circuit  22  is still large in scale, preventing the LCD apparatus from being compact in size. Also, since the output buffer circuit of the data driver circuit  22  has the same number of power consuming amplifiers (voltage followers) as the data lines DL 1 , DL 2 , . . . , DL m , the power consumption is enormously increased. 
     In  FIG. 16 , which illustrates a first embodiment of the LCD apparatus according to the present invention, reference numeral  1  designates an LCD panel having m×n dots where m is 640 and n is 480, for example. That is, the LCD panel  1  includes m data lines DL 1 , DL 2 , DL 3 , DL 4 , . . . , DL m−1 , DL m  driven by a data line driver circuit  2 , (n+1) gate lines GL 1 , GL 2 , GL 3 , GL 4 , . . . , GL n−1 , GL n , GL n+1 , and m×n pixels P ij  located at intersections between the data lines DL 1 , DL 2 , DL 3 , DL 4 , . . . , DL n−1 , DL n  and the gate lines GL 1 , GL 2 , GL 3 , GL 4 , . . . , GL n−1 , GL n , GL n+1 , The gate line GL n+1  is additional to the gate lines GL 1 , GL 2 , GL 3 , GL 4 , . . . , GL n−1 , GL n  of  FIGS. 1 and 10 ; however, this would never increase the manufacturing steps. 
     Each of the pixels P ij  is constructed by two TFTs Q ij  and Q ij ′ and one pixel capacitor C ij  including liquid crystal connected to a common electrode to which the common electrode voltage VCOM is applied. The TFT Q ij  is connected between the data line DL i  and the TFT Q ij ′, and the TFT Q ij ′ is connected between the TFT Q ij  and the pixel capacitor C ij . 
     If i+j=2, 4, 6, . . . , the pixel P ij  is of a first type where the gate of the TFT Q ij  such as Q 11  is connected to the gate line GL j  such as GL 1  and the gate of the TFT Q ij ′ such as Q 11 ′ is connected to the gate line GL j+1  such as GL 2 . Therefore, when the voltages at the gate lines GL j  and GL j+1  are both high, video data or black data is supplied from the data line DL i  to the first type pixel P ij  (i+j=2, 4, 6, 8, . . . ). 
     On the other hand, if i+j=3, 5, 7, 9, . . . , the pixel P ij  is of a second type where the gates of the TFT Q ij  and Q ij ′ such as Q 21  and Q 21 ′ are both connected to the gate line GL j  such as GL 1 . Therefore, when the voltage at the gate line GL j  is high, video data or black data is supplied from the data line DL i  to the second type pixel P ij  (i+j=3, 5, 7, 9, . . . ). 
     The first type pixels P ij  (i+j=2, 4, 6, 8, . . . ) and the second type pixels P i j  (i+j=3, 5, 7, 9, . . . ) are staggered in the LCD panel  1 . That is, the first type pixels P ij  (i+j=2, 4, 6, 8, . . . ) and the second type pixels P ij  (i+j=3, 5, 7, 9, . . . ) are alternately arranged in rows, columns. 
     In  FIG. 17 , which illustrates a detailed circuit diagram of the data line driver circuit  2  of  FIG. 16 , the data line driver circuit  2  is constructed by a shift register circuit  21 , a data register circuit  22 , a data latch circuit  23 , a digital/analog conversion circuit  24 , a black data voltage generation circuit  25 , and an output buffer circuit  26 . 
     The shift register circuit  21  shifts a horizontal start pulse signal HST as shown in  FIG. 18  in synchronization with a horizontal clock signal HCK as shown in  FIG. 18 . The shift register circuit  21  is formed by serially-connected D-type flip-flops  211 ,  212 , . . . ,  21   m/ 2 clocked by rising edges of the horizontal clock signal HCK to generate latch signals LA 1 , LA 2 , . . . , LAm/2, sequentially as shown in  FIG. 18 . Note that two horizontal start pulse signals HST are generated per one horizontal synchronization signal HSYNC from a horizontal timing generating circuit (not shown) which receives the horizontal synchronization signal HSYNC. Also, the horizontal clock signal HCK is generated from a clock signal generating circuit (not shown). 
     The data register circuit  22  latches an 8-bit gradation video data signal VD represented by B 0 , B 1 , . . . , B 7  in accordance with the latch signals LA 1 , LA 2 , . . . , LAm/2. The data register circuit  22  is formed by 8 D-type flip-flops  221  clocked by the latch signal LA 1  to latch digital video data D 1  or D 2  of the gradation video signal VD as shown in  FIG. 18 , 8 D-type flip-flops  222  clocked by the latch signal LA 2  to latch digital video data D 3  or D 4  of the gradation video signal VD as shown in  FIG. 18 , . . . , 8 D-type flip-flops  22  clocked by the latch signal LA 1   m/ 2 to latch digital video data Dm−1 or Dm of the gradation video signal VD as shown  FIG. 18 . In this case, the digital video data D 1 , D 3 , . . . , Dm−1, D 2 , D 4 , . . . , Dm of the 8 bit gradation video signal VD are sequentially generated from a signal processing circuit (not shown). In more detail, in a first horizontal period, the digital video data D 1 , D 3 , . . . , Dm−1, D 2 , D 4 , . . . , Dm are sequentially generated, and in a second horizontal period alternately with the first horizontal period, the digital video data D 2 , D 4 , . . . , Dm, D 1 , D 3 , . . . , Dm−1 are sequentially generated. 
     The data latch circuit  23  latches the digital video data D 1  or D 2 , D 3  or D 4 , . . . , Dm−1 or Dm. The data latch circuit  23  is formed by latch circuits  231 ,  232 ,  23   m/ 2 clocked by a horizontal strobe signal HSTB as shown in  FIG. 18  which is generated from the horizontal timing generating circuit. 
     The D/A conversion circuit  24  is formed by multiplexers  2411 ,  2412 , . . . ,  241   m/ 2 clocked by a polarity signal POL as shown in  FIG. 18 , positive-side D/A converters  2421 ,  2423 , . . . ,  242   m− 1 for generating analog gradation voltages on the positive side with respect to the common voltage VCOM, negative-side D/A converters  2422 ,  2424 ,  242   m  for generating analog gradation voltages on the negative side with respect to the common voltage VCOM, and multiplexers  2431 ,  2432 , . . . ,  243   m/ 2 clocked by the polarity signal POL. That is, if POL=“1”, the positive-side D/A converters  2421 ,  2423 ,  242   m− 1 are selected by the multiplexers  2411 ,  2412 , . . . ,  241   m/ 2 and the multiplexers  2431 ,  2432 , . . . ,  243   m/ 2. As a result, the D/A conversion circuit  24  generates positive polarity analog video signals corresponding to the digital video signals D 1  or D 2 , D 3  or D 4 , . . . , Dm−1 or Dm, respectively, and transmits them to the output buffer circuit  26 . On the other hand, if POL=“0”, the negative-side D/A converters  2422 ,  2424 ,  242   m  are selected by the multiplexers  2411 ,  2412 , . . . ,  241   m/ 2 and the multiplexers  2431 ,  2432 , . . . ,  243   m/ 2. As a result, the D/A conversion circuit  24  generates negative polarity analog video signals corresponding to the digital video signals D 1  or D 2 , D 3  or D 4 , . . . , Dm−1 or Dm, respectively, and transmits them to the output buffer circuit  26 . 
     The black data voltage generation circuit  25  is formed by a multiplexer  251  clocked by the polarity signal POL and an amplifier  252 . The multiplexer  251  operates in the same way as the multiplexers  2411 ,  2412 , . . . ,  241   m/ 2 and the multiplexers  2431 ,  2432 , . . . ,  243   m/ 2. That is, if POL=“1”, black data B− is selected, amplified and transmitted to the output buffer circuit  26 . On the other hand, if POL=“0”, black data B+ is selected, amplified and transmitted to the output buffer circuit  26 . 
     The output buffer circuit  26  multiplexes the analog video signals from the D/A conversion circuit  24  and the black data voltage B− or B+ in accordance with a data selection signal DSL which is nearly equal to a signal obtained by dividing the polarity signal POL. The data selection signal DSL is generated from the horizontal timing generating circuit. 
     The output buffer circuit  26  is formed by amplifiers (usually, voltage-follower-type operational amplifiers)  2611 ,  2612 , . . . ,  261   m/ 2 for amplifying the analog video signals from the multiplexers  2431 ,  2432 , . . . ,  243   m/ 2, respectively, of the D/A conversion circuit  24  and multiplexers  2621 ,  2622 , . . . ,  262   m/ 2 clocked by the data selection signal DSL. In this case, if DSL=“1”, the multiplexers  2621 ,  2622 , . . . ,  262   m/ 2 are in a through state, while, if DSL=“0”, the multiplexers  2621 ,  2622 , . . . ,  262   m/ 2 are in a cross state. 
     Therefore, in a first horizontal period, when POL=“1” (positive) and DSL=“1” (through state), signals D 1 (+), B−, D 3 (+), B−, . . . , Dm−1(+), B− and generated from the output buffer circuit  26 , and subsequently, when POL=“0” (negative) and DSL=“0” (cross state), signals B+, D 2 (−), B+, D 4 (−), . . . , B+, Dm(−) are generated from the output buffer circuit  26 . 
     On the other hand, in a second horizontal period, when POL=“1” (positive) and DSL=“0” (cross state), signals B−, D 2 (+), B−, D 4 (+), . . . , B−, Dm(+) are generated from the output buffer circuit  26 , and subsequently, when POL=“0” (negative) and DSL=“1” (through state), signals D 1 (−), B+, D 3 (−), B 4 , . . . , Dm−1(−), B+ are generated from the output buffer circuit  26 . 
     In  FIG. 19 , which illustrates a detailed circuit diagram of the gate line driver circuit  2  of  FIG. 16 , the gate line driver circuit  3  is constructed by shift register circuits  31  and  32  for shifting a vertical start pulse signal VST as shown in  FIG. 20  in synchronization with a vertical clock signal VCK as shown in  FIG. 20 , a gate circuit  33  and an output buffer circuit  34  formed by amplifiers  341 ,  342 ,  343 ,  344 , . . . ,  34   n− 1,  34   n . Note that two vertical start pulse signals VST are generated per one frame period. 
     The shift register circuit  31  is formed by serially-connected D-type flip-flops  311 ,  312 ,  313 ,  314 , . . . ,  31   n− 1,  30   n ,  31   n+ 1,  31   n+ 2 clocked by rising edges of the vertical clock signal VCK to generate signals S 1 , S 2 , S 3 , S 4 , . . . , S n−1 , S n , S n+1 , S n+2  as shown in  FIG. 20 . 
     The shift register circuit  32  is formed by serially-connected D-type flip-flops  321 ,  322 ,  323 ,  324 , . . . ,  32   n− 1,  32   n ,  32   n+ 1 clocked by falling edges of the vertical clock signal VCK to generate signals S 1 ′, S 2 ′, S 3 ′, S 4 ″, . . . , S n−1 ′, S n ″, S n+1 ′ as shown in  FIG. 20 . 
     The gate circuit  33  is formed by a gate  331  for receiving the signals S 1 ′ and S 2 , a gate  332  for receiving the signals S 2 ′ and S 3 , a gate  333  for receiving the signals S 3 ′ and S 4 , a gate  334  for receiving the signals S 4 ′ and S 5 , . . . , a gate  33   n− 1 for receiving the signals S n−1 ′ and S n , a gate  33   n  for receiving the signals S n ′ and S n+1 , and a gate  33   n− 1 for receiving the signals S n+1 ′ and S n+2 . Also, the gate circuit  33  is formed by a gate  331 ′ for receiving the signal S 1  and an output signal S 1 ″ of the gate  331 , a gate  332 ′ for receiving the signal S 2  and an output signal S 2 ″ of the gate  332 , a gate  333 ′ for receiving the signal S 3  and an output signal S 3 ″ of the gate  333 , a gate  334 ′ for receiving the signal S 4  and an output signal S 4 ″ of the gate  334 , . . . , a gate  33   n− 1′ for receiving the signal S n−1  and an output signal S m−1 ″ of the gate  33   n− 1, a gate  33   n ′ for receiving the signal S n  and an output signal S n ″ of the gate  33   n , and a gate  33   n− 1′ for receiving the signal S n+1  and an output signal S n+1 ″ of the gate  33   n− 1. 
     Thus, the gate circuit  33  generates gate line signals (or scan line signals) on the gate lines GL 1 , GL 2 , GL 3 , GL 4 , . . . , GL n−1 , GL n , GL n+1 , respectively, as shown in  FIG. 20 . 
     As shown in  FIG. 20 , two vertical start pulse signals VST are generated per one frame period. A first one of the vertical start pulse signals VST is used for writing black data, while a second one of the vertical start pulse signals VST is used for writing video data. 
     As illustrated in  FIG. 21 , in the former half T 1  of a first frame period, when video data {circle around (1)}+ and {circle around (3)}+ are supplied to the data lines DL 1  and DL 3 , respectively, and black data B− is supplied to the data lines DL 2  and DL 4  while the gate line signals at the gate lines GL 1 , GL 2 , GL k+1  and GL k+2  are high, the video data {circle around (1)}+ is written into pixels A, E and BA, the video data {circle around (3)}+ is written into pixels C, G and BC, and black data B− is written into pixels B, D, BB, BD, BF and BH, at time t 1  as illustrated in  FIG. 22 . Subsequently, in the latter half T 1 ′ of the first frame period, when video data {circle around (2)}− and {circle around (4)}− and supplied to the data lines DL 2  and DL 4 , respectively, and black data B+ is supplied to the data lines DL 1  and DL 3  while the gate line signals at the gate lines GL 1  and GL k+1  are high, the video data {circle around (2)}− is written into pixel B, the video data {circle around (4)}− is written into pixel D, and black data B+ is written into pixels BA and BC, at time t 1 ′ as illustrated in  FIG. 22 . 
     Next, in the former half T 2  of a second frame period, when video data {circle around (2)}′+ and {circle around (4)}′+ are supplied to the data lines DL 2  and DL 4 , respectively, and black data B− is supplied to the data lines DL 1  and DL 3  while the gate line signals at the gate lines GL 2 , GL 3 , GL k+2  and GL k+3  are high, the video data {circle around (2)}′+ is written into pixels F, J and BF, the video data {circle around (4)}′+ is written into pixels H, L and BH, and black data B− is written into pixels E, G, BE, BI, BG and BK, at time t 2  as illustrated in  FIG. 22 . Subsequently, in the latter half T 2 ′ of the second frame period, when video data {circle around (1)}′− and {circle around (3)}′− and supplied to the data lines DL 1  and DL 3 , respectively, and black data B+ is supplied to the data lines DL 2  and DL 4  while the gate line signals at the gate lines GL 2  and GL k+2  are high, the video data {circle around (1)}′− is written into pixel E, the video data {circle around (3)}′− is written into pixel G, and black data B+ is written into pixels BF and BH, at time t 2 ′ as illustrated in  FIG. 22 . 
     Next, in the former half T 3  of a third frame period, when video data {circle around (1)}″+ and {circle around (3)}″+ are supplied to the data lines DL 1  and DL 3 , respectively, and black data B− is supplied to the data lines DL 2  and DL 4  while the gate line signals at the gate lines GL 3 , GL 4 , GL k+3  and GL k+4  are high, the video data {circle around (1)}″+ is written into pixels I, M and BI, the video data {circle around (3)}″+ is written into pixels K, O and BK, and black data B− is written into pixels J, L, BJ, BN, BL and BP, at time t 3  as illustrated in  FIG. 22 . Subsequently, in the latter half T 3 ′ of the third frame period, when video data {circle around (2)}″− and {circle around (4)}″− and supplied to the data lines DL 2  and DL 4 , respectively, and black data B+ is supplied to the data lines DL 1  and DL 3  while the gate line signals at the gate lines GL 3  and GL k+3  are high, the video data {circle around (2)}″− is written into pixel J, the video data {circle around (4)}″− is written into pixel L, and black data B+ is written into pixels BI and BK, at time t 3 ′ as illustrated in  FIG. 22 . 
     Thereafter, the same operation as described above is repeated. 
     Thus, in the same way as in the second prior art LCD apparatus of  FIG. 10 , a black region having a width of k gate lines where k=1, 3, 5, . . . is scanned to suppress the residual image phenomenon. 
     In the LCD apparatus of  FIG. 16 , since the data line driver circuit  2  of  FIG. 17  has a smaller configuration than the data line driver circuit  12  of  FIG. 2 , the data line driver circuit  2  can be small in size, so that the integration can be enhanced. Also, since the output buffer circuit  26  of  FIG. 17  has half the number of power consuming amplifiers as that of the data lines DL 1 , DL 2 , . . . , DL m , the power consumption can be remarkably reduced. 
     In  FIG. 23 , which illustrates a second embodiment of the LCD apparatus according to the present invention, the LCD panel  1  of  FIG. 16  is replaced by an LCD panel  1 ′ where the first type of two consecutive pixels P ij  (i=1, 2, 5, 6, . . . under j=1, 3, 5, . . . , and i=3, 4, 7, 8, . . . under j=2, 4, 6, . . . ) and the second type of two consecutive pixels P ij  (i=3, 4, 7, 8, . . . under j=1, 3, 5, . . . , and i=1, 2, 5, 6, . . . under j=2, 4, 6, are staggered. That is, two first type pixels P ij  and two second type pixels P ij  are alternately arranged in rows, columns. 
     Each of the first type pixels P ij  is the same as those of  FIG. 16 . That is, the gate of the TFT Q ij  such as Q 11  is connected to the gate line GL j  such as GL 1  and the gate of the TFT Q ij ′ such as Q 11 ′ is connected to the gate line GL j+1  such as GL 2 . Therefore, when the voltages at the gate lines GL j  and GL j+1  are both high, video data or black data is supplied from the data line DL i  to the first type pixel P ij . 
     Also, each of the second type pixels P ij  is the same as those of  FIG. 16 . That is, the gates of the TFT Q ij  and Q ij ′ such as Q 22  and Q 22 ′ are both connected to the gate line GL j  such as GL 2 . Therefore, when the voltage at the gate line GL j  is high, video data or black data is supplied from the data line DL i  to the second type pixel P i j . 
     Also, in  FIG. 23 , the data line driver circuit  2  of  FIG. 16  is replaced by a data line driver circuit  2 ′ which is illustrated in  FIG. 24  in detail. 
     In  FIG. 17 , the data line driver circuit  2 ′ is constructed by a shift register circuit  21 ′, a data register circuit  22 ′, a data latch circuit  23 ′, a D/A conversion circuit  24 ′, a black data voltage generation circuit  25 ′, and an output buffer circuit  26 ′. 
     The shift register circuit  21 ′ shifts a horizontal start pulse signal HST as shown in  FIG. 25  in synchronization a horizontal clock signal HCK as shown in  FIG. 25 . The shift register circuit  21 ′ has the same configuration as the shift register circuit  21  of  FIG. 17 . That is, the shift register circuit  21 ′ is formed by serially-connected D-type flip-flops  211 ,  212 , . . . ,  21 ( m/ 2−1),  21   m/ 2 clocked by rising edges of the horizontal clock signal HCK to generate latch signals LA 1 , LA 2 , . . . LA(m/2−1), LAm/2, sequentially as shown in  FIG. 25 . 
     The data register circuit  22 ′ latches an 8-bit gradation video data signal VD represented by B 0 , B 1 , . . . , B 7  in accordance with the latch signals LA 1 , LA 2 , . . . , LA(m/2−1), LAm/2. The data register circuit  22 ′ has the same configuration as the data register circuit  22  of  FIG. 17 . That is, the data register circuit  22 ′ is formed by 8 D-type flip-flops  221  clocked by the latch signal LA 1  to latch digital video data D 1  or D 3  of the gradation video signal VD as shown in  FIG. 25 , 8 D-type flip-flops  222  clocked by the latch signal LA 2  to latch digital video data D 3  or D 4  of the gradation video signal VD as shown in  FIG. 25 , . . . , 8 D-type flip-flops  22  (m/2−1) clocked by the latch signal LA(m/2−1) to latch digital video data Dm−3 or Dm−2 of the gradation video signal VD as shown in  FIG. 25 , and 8 D-type flip-flops  22  clocked by the latch signal LAm/2 to latch digital video data Dm−2 or Dm of the gradation video signal VD as shown in  FIG. 25 . In this case, the digital video data D 1 , D 2 , D 5 , . . . , Dm−3, Dm−2, D 3 , D 4 , D 7 , . . . , Dm−1, Dm of the 8 bit gradation video signal VD are sequentially generated from a signal processing circuit (not shown). In more detail, in a first horizontal period, the digital video data D 1 , D 2 , D 5 , . . . , Dm−3, Dm−2, D 3 , D 4 , D 7 , . . . , Dm−1, Dm are sequentially generated, and in a second horizontal period, alternately with the first horizontal period, the digital video data D 3 , D 4 , D 7 , . . . Dm−1, Dm, D 1 , D 2 , D 5 , . . . , Dm−3, Dm−2 are sequentially generated. 
     The data latch circuit  23 ′ latches the digital video data D 1  or D 3 , D 2  or D 4 , . . . , Dm−3 or Dm−1, Dm−2 or Dm. The data latch circuit  23 ′ has the same configuration as the data latch circuit  23  of  FIG. 17 . That is, the data latch circuit  23 ′ is formed by latch circuits  231 ,  232 , . . . ,  23 ( m/ 2−1),  23   m/ 2 clocked by a horizontal strobe signal HSTB as shown in  FIG. 25  which is generated from the horizontal timing generating circuit. 
     The D/A conversion circuit  24 ′ has the same configuration as the D/A conversion circuit  24  of  FIG. 17 . That is, the D/A conversion circuit  24 ′ is formed by multiplexers  2411 , . . . ,  241   m/ 2 clocked by a polarity signal POL as shown in  FIG. 25 , positive-side D/A converters  2421 , . . . ,  242   m− 1 for generating analog gradation voltages on the positive side with respect to the common voltage VCOM, negative-side D/A converters  2422 , . . . ,  242   m  for generating analog gradation voltages on the negative side with respect to the common voltage VCOM, and multiplexers  2431 ,  2432 , . . . ,  243   m/ 2 clocked by the polarity signal POL. That is, if POL=“1”, the positive-side D/A converters  2421 , . . . ,  242   m− 1 are selected by the multiplexers  2411 , . . . ,  241   m/ 2 and the multiplexers  2431 , . . . , −,  243   m/ 2. As a result, the D/A conversion circuit  24 ′ generates positive polarity analog video signals corresponding to the digital video signals D 1  or D 3 ,. D 2  or D 4 , . . . , Dm−3 or Dm−1, Dm−2 or Dm, respectively, and transmits them to the output buffer circuit  26 ′. On the other hand, if POL=“0”, the negative-side D/A converters  2422 , . . . ,  242   m  are selected by the multiplexers  2411 , . . . ,  241   m/ 2 and the multiplexers  2431 , . . . ,  243   m/ 2. As a result, the D/A conversion circuit  24 ′ generates negative polarity analog video signals corresponding to the digital video signals D 1  or D 3 , D 2  or D 4 , . . . , Dm−3 or Dm−1, Dm−2 or Dm, respectively, and transmits them to the output buffer circuit  26 . 
     The black data voltage generation circuit  25 ′ is similar to the black data voltage generation circuit  25  of  FIG. 17 . That is, the black data voltage generation circuit  25 ′ is formed by a multiplexer  251  clocked by the polarity signal POL and amplifiers  252  and  253 . The multiplexer  251  operates in the same way as the multiplexers  2411 , . . . ,  241   m/ 2 and the multiplexers  2431 , . . . ,  243   m/ 2. Therefore, if POL=“1”, black data B+ and B− are amplified and transmitted to the output buffer circuit  26 ′. On the other hand, if POL=“0”, black data B− and B+ are amplified and transmitted to the output buffer circuit  26 ′. 
     The output buffer circuit  26 ′ multiplexes the analog video signals from the D/A conversion circuit  24 ′ and the black data voltage B+ or B− in accordance with a data selection signal DSL which is generated from the horizontal timing generating circuit. 
     The output buffer circuit  26 ′ is similar to the output buffer circuit  26  of  FIG. 17 . That is, the output buffer circuit  26 ′ is formed by amplifiers  2611 ,  2612 , . . . ,  261 ( m/ 2−1),  261   m/ 2 for amplifying the analog video signals from the multiplexers  2431 , . . . ,  243   m/ 2, of the D/A conversion circuit  24 ′ and multiplexers  2621 , . . . ,  262   m/ 4 clocked by the data selection signal DSL. In this case, if DSL=“1”, the multiplexers  2621 , . . . ,  262   m/ 4 are in a through state, while, if DSL=“0”, the multiplexers  2621 ,  262   m/ 4 are in a cross state. 
     Therefore, in a first horizontal period, when POL=“1” (positive) and DSL=“1” (through state), signals D 1 (+), D 2 (−), B+, B−, . . . , Dm−3(+), Dm−2(−), B+, B− and generated from the output buffer circuit  26 ′, and subsequently, when POL=“1” (positive) and DSL=“0” (cross state), signals B+, B−, D 3 (+), D 4 , . . . , B+, B−, Dm−1(+), Dm(−) are generated from the output buffer circuit  26 ′. 
     Therefore, in a second horizontal period, when POL=“0” (negative) and DSL=“0” (cross state), signals B−, B+, D 3  (−), D 4 (+), . . . , B−, B+, Dm−1(−), Dm(+) are generated from the output buffer circuit  26 ′, and subsequently, when POL=“0” (negative) and DSL=“1” (through state), signals D 1 (−), D 2 (+), B−, B+, . . . , Dm−3(−) Dm−2(+), B−, B+ are generated from the output buffer circuit  26 ′. 
     Note that the gate line driver circuit  3  has the same configuration as that of  FIG. 17 . 
     As illustrated in  FIG. 26 , in the former half T 1  of a first frame period, when video data {circle around (1)}+ and {circle around (2)}− are supplied to the data lines DL 1  and DL 2 , respectively, and black data B+ and B− and supplied to the data lines DL 3  and DL 4  while the gate line signals at the gate lines GL 1 , GL 2 , GL k+1  and GL k+2  are high, the video data {circle around (1)}+ is written into pixels A, E and BA, the video data {circle around (2)}− is written into pixels B, F and BB, black data B+ is written into pixels C, BC and BG, and black data B− is written into pixels D, BD and BH, at time t 1  as illustrated in  FIG. 27 . Subsequently, in the latter half T 1 ′ of the first frame period, when video data {circle around (3)}+ and {circle around (4)}− and supplied to the data lines DL 3  and DL 4 , respectively, and black data B+ and B− and supplied to the data lines DL 1  and DL 2  while the gate line signals at the gate lines GL 1  and GL k+1  are high, the video data {circle around (3)}+ is written into pixel C, the video data {circle around (4)}− is written into pixel D, black data B+ is written into pixel BA, and black data B− is written into pixel BB at time t 1 ′ as illustrated in  FIG. 27 . 
     Next, in the former half T 2  of a second frame period, when video data {circle around (3)}′− and {circle around (4)}′+ are supplied to the data lines DL 3  and DL 4 , respectively, and black data B− and B+ are supplied to the data lines DL 1  and DL 2  while the gate line signals at the gate lines GL 2 , GL 3 , GL k+2  and GL k+3  are high, the video data {circle around (3)}′− is written into pixels G, K and BG, the video data {circle around (4)}′+ is written into pixels G, L and BH, black data B− is written into pixels E, BE and BI, and black data B+ is written into pixels F, BF and BJ at time t 2  as illustrated in  FIG. 27 . Subsequently, in the latter half T 2 ′ of the second frame period, when video data {circle around (1)}′− and {circle around (2)}′+ are supplied to the data lines DL 1  and DL 2 , respectively, and black data B− and B+ are supplied to the data lines DL 3  and DL 4  while the gate line signals at the gate lines GL 2  and GL k+2  are high, the video data {circle around (1)}′− is written into pixel E, the video data {circle around (2)}′+ is written into pixel F, black data B+ is written into pixel BG, and black data B+ is written into pixels BH, at time t 2 ′ as illustrated in  FIG. 27 . 
     Next, in the former half T 3  of a third frame period, when video data {circle around (1)}″+ and {circle around (2)}″− and supplied to the data lines DL 1  and DL 2 , respectively, and black data B+ and B− and supplied to the data lines DL 3  and DL 4  while the gate line signals at the gate lines GL 3 , GL 4 , GL k+3  and GL k+4  are high, the video data {circle around (1)}″+ is written into pixels I, KM and I, the video data {circle around (2)}″− is written into pixels J, O and BK, black data B+ is written into pixels K, BK and BO, and black data B− is written into pixels L, BL and BP, at time t 3  as illustrated in  FIG. 27 . Subsequently, in the latter half T 3 ′ of the third frame period, when video data {circle around (3)}″+ and {circle around (4)}″− and supplied to the data lines DL 3  and DL 4 , respectively, and black data B+ and B− and supplied to the data lines DL 1  and DL 2  while the gate line signals at the gate lines GL 3  and GL k+3  are high, the video data {circle around (3)}″+ is written into pixel K, the video data {circle around (4)}″− is written into pixel L, black data B+ is written into pixel BI, and black data B− is written into pixel BJ, at time t 3 ′ as illustrated in  FIG. 27 . 
     Thereafter, the same operation as described above is repeated. 
     Thus, in the same way as in the second prior art LCD apparatus of  FIG. 10 , a black region having a width of k gate lines where k=1, 3, 5, . . . is scanned to suppress the residual image phenomenon. 
     Even in the LCD apparatus of  FIG. 23 , since the data line driver circuit  2 ′ of  FIG. 24  has a smaller configuration than the data line driver circuit  12  of  FIG. 2 , the data line driver circuit  2 ′ can be small in size, so that the integration can be enhanced. Also, since the output buffer circuit  26 ′ of  FIG. 24  has half the number of power consuming amplifiers as that of the data lines DL 1 , DL 2 , . . . , DL m , the power consumption can be remarkably reduced. 
     In the above-described embodiments, although the black data voltage B+ or B− is set to be a maximum voltage or a minimum voltage in a normal white type LCD apparatus, the present invention can be applied to a normal black type LCD apparatus where the black data voltage B+ or B− is set to be the common voltage VCOM. 
     Also, in the above-described embodiments, the second type pixel includes two TFTs connected to one gate line; however, this second type pixel can include one TFT whose ON resistance is equivalent to the two TFTs. 
     Further, in the above-described embodiments, the locations of the first type pixels and the locations of the second type pixels can be exchanged with each other. In this case, the operation for the first horizontal period and the operation for the second horizontal period are exchanged with other. 
     Still, in the above-described embodiments, one or two first type pixels and one or two second type pixels are staggered; however, three or more first type pixels and three or more second type pixels can be staggered. 
     Furthermore, in the above-described embodiments, inversion methods other than the dot inversion method can be adopted. 
     Additionally, the present invention can be applied to hold type image display apparatuses other than an LCD apparatus, such as an electroluminescence (EL) display apparatus. 
     As explained hereinabove, according to the present invention, the data line driver circuit can be small in size and its power consumption can be reduced.