Abstract:
A sun tanning apparatus has an electronic operating system comprising: (i) a plurality of pairs of fluorescent lamps for providing tanning radiation, each pair of lamps being adapted to be powered from 30 kHz/120 Volt by way of a high-Q series-resonant L-C ballasting circuit; (ii) a relatively low-power frequency converter connected with the power line and operable to provide power for heating the cathodes in these fluorescent lamps, thereby conditioning the lamps for easy starting; (iii) a relatively high-power frequency converter also connected with a power line and operable to provide the 30 kHz/120 Volt required for operating the plurality of pairs of fluorescent lamps by way of the high-Q series-resonant L-C ballasting circuit; and (iv) delay means operable to prevent the 30 kHz/120 Volt provided by the high-power frequency converter from being applied to the fluorescent lamps until after power has been applied to heat the lamp cathodes for at least one second. Each high-Q series-resonant L-C ballast circuit is protected from over-voltages by a Varistor, which acts as a substitute load in case a lamp is removed or fails to operate properly. If current should flow through one of the Varistors for more than a few milli-seconds, the high-power frequency converter is disabled, thereby removing the 30 kHz/120 Volt.

Description:
BACKGROUND OF THE INVENTION 
     1 Field of Invention 
     The present invention relates to operating systems for sun tanning and other skin treatment apparatus, particularly of the kind using a plurality of fluorescent lamps. 
     2 Prior Art 
     An ordinary sun tanning bed or booth typically comprises between 20 and 40 fluorescent lamps, with each lamp being 72&#34; long and requiring about 100 Watt of power input for effective operation. These lamps are powered by way of a plurality of individual ballasts, with each ballast powering one or two lamps. 
     The fluorescent lamps used are of the so-called rapid-start type; which implies that each lamp requires four supply wires for proper operation. As a result, the number of wires required for powering 20-to-40 fluorescent lamps gets to be very high. 
     SUMMARY OF THE INVENTION 
     Brief Description 
     Subject invention constitutes an operating system for a sun tanning apparatus. In its preferred embodiment, this operating system is adapted to be powered from an ordinary electric utility power line and comprises: 
     (a) special fluorescent lamps for providing skin tanning radiation, these lamps being arranged in the form of a plurality of separately identifiable lamp lamp-ballast assemblies, each such assembly having: (i) a pair of fluorescent lamps, (ii) a high-Q series-resonant L-C ballasting circuit operable to power the pair of lamps from 30 kHz/120 Volt, and (iii) a first and a second set of assembly terminals, one set located at each end of the assembly; 
     (b) a central frequency-converting power supply connected with said power line and having: (i) a relatively low-power frequency converter operable to provide a first 30 kHz/120 Volt AC voltage for heating the cathodes in these fluorescent lamps, thereby to condition the lamps for easy starting, (ii) a relatively high-power frequency converter operable to provide a second 30 kHz/120 Volt AC voltage for operating the plurality of lamp-ballast assemblies, and (iii) a first and a second set of central terminals; 
     (c) a first and a second distribution conductor means operable to provide connection between said first and second sets of central terminals and said first and second sets of assembly terminals; and 
     (iv) delay means operable to prevent the second 30 kHz/120 Volt AC voltage from being applied to the lamp assemblies until after the first 30 kHz/120 Volt AC voltage has had an opportunity to heat the lamp cathodes for at least one second. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 provides a schematic illustration of the central frequency-converting power supply. 
     FIG. 2 diagrammatically describes the overall operating system in its preferred embodiment, including the central power supply, two sets of distribution conductors coming therefrom, and plural lamp-ballast assemblies connected between these two sets of distribution conductors. 
     FIG. 3 provides schematic details of a lamp-ballast assembly. 
    
    
     DESCRIPTION OF THE PREFERRED EMBODIMENT 
     Details of Construction 
     FIG. 1 shows an AC voltage source S, which in reality is an ordinary 120 Volt/60 Hz electric utility power line. 
     Connected to S is a full-wave rectifier FWR that rectifies the AC voltage from S to provide an unfiltered DC voltage between a positive power bus B+ and a negative power bus B-. 
     A first pair of transistors Q1a and Q1b are connected in series between the B+ bus and the B- bus in such a way that the collector of Q1a is connected to the B+ bus, the emitter of Q1a is connected with the collector of Q1b at a juction J1, and the emitter of Q1b is connected with the B- bus. 
     A second pair of transistors Q2a and Q2b are connected in series between the B+ bus and the B- bus in such a way that the collector of Q2a is connected to the B+ bus, the emitter of Q2a is connected with the collector of Q2b at a junction J2, and the emitter of Q2b is connected with the B- bus. 
     Primary winding FT1ap of saturable feedback transformer FT1a and primary winding FT1bp of saturable feedback transformer FT1b are connected in series between junction J1 and output terminal OT1x. Another output terminal OT1y is connected with junction JC between capacitors Ca and Cb; which capacitors are connected in series between the B+ bus and the B- bus. 
     Primary winding FT2ap of saturable feedback transformer FT2a and primary winding FT2bp of saturable feedback transformer FT2b are connected in series between junction J2 and output terminal OT2y. Another output terminal OT2x is connected with junction JC. 
     Secondary winding FT1as of feedback transformer FT1a is connected between the base and the emitter of transistor Q1a; and secondary winding FT1bs of feedback transformer FT1b is connected between the base and the emitter of transistor Q1b. 
     Secondary winding FT2as of feedback transformer FT2a is connected between the base and the emitter of transistor Q2a; and secondary winding FT2bs of feedback transformer FT2b is connected between the base and the emitter of transistor Q2b. 
     A resistor R1 is connected between the B+ bus and a junction DJ1; and a capacitor C1 is connected between junction DJ1 and the B- bus. A Diac D1 is connected between junction DJ1 and the base of transistor Q1b. 
     A series-combination of a normally-open thermally-activated switch NOTAS and a resistor R2 is connected between the B+ bus and a junction DJ2. This switch also has two auxiliary terminals AT1 and AT2 connected directly between the B+ bus and the B- bus. A capacitor C2 is connected between junction DJ2 and the B- bus. A Diac D2 is connected between junction DJ2 and the base of transistor Q2b. 
     A control transistor Qc is connected with its collector to junction DJ2 and its emitter to the B- bus. A series-combination of a resistor R3 and a Diac D3 is connected between a junction DJ3 and the base of transistor Qc. A capacitor C3 is connected between junction DJ3 and the B- bus. A resistor R4 is connected between junction DJ3 and first control input terminal CIT1. A resistor R5 is connected between first control input terminal CIT1 and a second control input terminal CIT2; which second control input terminal is connected with the B- bus. 
     Primary winding T1p of a transformer T1 is connected between inverter output terminals OT1x and OT1y. Secondary winding T1s is connected between cathode power output terminals CPOT1 and CPOT2. 
     Primary winding T2p of a transformer T2 is connected between inverter output terminals OT2x and OT2y. Secondary winding T2s is connected between terminal OT2y and a main power output terminal MPOT2. A main power output terminal MPOT1 is connected directly with inverter output terminal OT2x. 
     A first set of central terminals CT1 has two individual central terminals CT1a and CT1b; which terminals are connected with terminals CPOT1 and CPOT2, respectively. 
     A second set of central terminals CT2 has five individual central terminals CT2a, CT2b, CT2c, CT2d and CT2e. Of these terminals, CT2a and CT2b are connected with CPOT1 and CPOT2 respectively; CT2b and CT2c are connected with MPOT1 and MPOT2, respectively; and CT2d and CT2e are connected with CIT1 and CIT2, respectively. 
     The assembly consisting of transistors Q1a and Q1b, feedback transformers FT1a and FT1b, and output terminals OT1x and OT1y is referred to as low power inverter LPI. The assembly consisting of transistors Q2a and Q2b, feedback transformers FT2a and FT2b, and output terminals OT2x and OT2y is referred to as high power inverter HPI. The overall power supply of FIG. 1 is referred to as central power supply CPS. 
     FIG. 2 shows a first and a second set of distribution conductor means DCM1 and DCM2 connected respectively with the first and the second set of central terminals CT1 and CT2 on central power supply CPS. 
     The first set of distribution conductor means comprises two individual distribution conductors DC1a and DC1b; which are connected with central terminals CT1a and CT1b, respectively. 
     The second set of distribution conductor means comprises five individual distribution conductors DC2a, DC2b, DC2c, DC2d and DC2e; which are connected with central terminals CT2a, CT2b, CT2c, CT2d and CT2e, respectively. 
     Located between and connected with the two distribution conductor means DCM1 and DCM2, are a plurality of lamp-ballast assemblies LBAm, LBAn--LBAx. Each lamp-ballast assembly comprises two lamp-ballast matching means: LBMm1 and LBMm2, LBMn1 and LBMn2--LBM×1 and LBM×2, respectively. 
     Lamp-ballast matching means LBMm1 has two terminals Tm1a and Tm1b; which are connected to distribution conductors DC1a and DC1b, respectively. Lamp-ballast matching means LBMm2 has five individual terminals Tm2a, Tm2b, Tm2c, Tm2d and Tm2e; which are connected to distribution conductors DC2a, DC2b, DC2c, DC2d and DC2e, respectively. 
     Similarly, lamp-ballast matching means LBMn1 has two terminals, lamp-ballast matching means LBMn2 has five terminals, lamp-ballast matching means LBM×l has two terminals, and lampballast matching means LBM×2 has five terminals; which terminals are all connected to individual distribution conductors in a manner that is analogous to the manner in which the terminals of lamp-ballast matching means LBNm1 and LBMm2 are connected. 
     FIG. 3 illustrates electric circuit details of lamp-ballast assembly LBAm. 
     A cathode transformer CTm1 has a primary winding CTm1p connected between terminals Tm1a and Tm1b; and it has a secondary winding CTm1s connected with the parallel-connected lamp cathodes LCm1&#39; and LCm1&#34; of fluorescent lamps FLm&#39; and FLm&#34;, respectively. 
     A capacitor Cm1 is connected between terminal Tm1a and one of the terminals of secondary winding CTm1s. 
     A cathode transformer CTm2 has a primary winding CTm2p connected between terminals Tm2a and Tm2b; and it has two secondary winding CTm2s&#39;and CTm2s&#34;connected with lamp cathodes LCm2&#39; and LCm2&#34; of fluorescent lamps FLm&#39; and FLm&#34;, respectively. 
     An inductor Lm is connected between terminal Tm2c and a junction Jm; and a capacitor Cm is connected between junction Jm and terminal Tm2b. Also connected with terminal Tm2b is one of the terminals of lamp cathode LCm2&#39;. A series-combination of a Varistor Vm and primary winding CTmp of a current transformer CTm is connected between terminal Tm2b and junction Jm. Secondary winding CTms of transformer CTm is connected between terminal Tm2e and the anode of a diode Dm2. The cathode of diode Dm2 is connected with terminal Tm2d. 
     DETAILS OF OPERATION 
     The operation of the central power supply CPS of FIG. 1 may be explained as follows. 
     FIG. 1 shows two half-bridge inverters: a low power inverter LPI consisting of transistors Q1a and Q1b with their respective saturable positive feedback transformers FT1a and FT1b; and a high power inverter HPI consisting of transistors Q2a and Q2b with their respective saturable positive feedback transformers FT2a and FT2b. 
     Both inverters are capable of self-oscillation by way of positive feedback. When they do oscillate, the frequency of oscillation is about 30 kHz. For further explanation of the operation of this type of inverter, reference is made to U.S. Pat. Nos. 4,184,l28 and 4,506,318, both issued to Nilssen. 
     Each of these inverters has to be triggered into oscillation; but they will on1y oscillate as long as the magnitude of the voltage between the B- bus and the B+ bus exceeds about 20 Volt. Thus, if one of the inverters is triggered into oscillation at the beginning of one of the sinusoidally-shaped DC voltage pulses existing between the B- bus and the B+ bus (as resulting from the unfiltered full-wave rectification of the voltage from the ordinary l20 Volt/60 Hz power line), that inverter will cease oscillating at the end of that DC voltage pulse. Thus, to keep either one of the inverters operating on a continuous basis, it is necessary that it be re-triggered at a rate of 120 times per second--i.e., once in the beginning of each half-cycle of the full-wave-rectified 120 Volt/60 Hz power line voltage. 
     Both the half-bridge inverters use capacitors Ca and Cb to provide for an effective center-tap between the B- bus and the B+ bus--this center-tap being junction JC. 
     When power line voltage is initially applied to the arrangement of FIG. 1, inverter LPI will immediately commence operation, receiving the requisite trigger pulses by way of trigger assembly R1/C1/D1. The time-constant associated with R1/C1 is such as to cause the voltage on C1 to reach a level high enough for Diac D1 to break down within about one millisecond after the beginning of each sinusoidally-shaped pulse provided by the full wave rectifier. Inverter HPI, on the other hand, will not start receiving trigger pulses--and therefore will not commence operation--until after the normally-open thermally-activated switch NOVAS has closed. In the preferred embodiment, the time required for this switch to close is about 1.5 second. Thereafter, however, inverter HPI starts receiving trigger pulses by way of trigger assembly R2/C2/D2. As with inverter LPI, the time-constant associated with R2/C2 is such as to cause the voltage on C2 to reach a level high enough for Diac D2 to break down within about one milli-second after the beginning of each sinusoidally-shaped pulse provided by the full wave rectifier. 
     Thus, the time required for capacitors C1 and C2 to be charged to Diac breakdown voltages is arranged to be but a small fraction of the length of a half-cycle of the 60 Hz power line voltage; which implies that both inverters will be triggered into oscillation at the beginning of each of the 120 Hz DC pulses provided between the B- bus and the B+ bus. 
     As a result of the relatively short time-constants, repeated triggering will occur during each complete DC pulse. While most often such repeated triggering is of little consequence, it is sometimes desirable to avoid it altogether; which may be accomplished by adding a first diode between junction DJ1 and the collector of transistor Q1b and a second diode between junction DJ2 and the collector of transistor Q2b--in both cases with the anodes of the diodes being connected with the junctions. 
     By applying current to the base of control transistor Qc, the voltage on capacitor C2 can be prevented from rising to a level high enough to cause Diac D2 to break down, thereby removing the trigger signals from the base of transistor Q2b,  which therefore prevents inverter HPI from being triggered into operation at the beginning of each of the 120 Hz DC voltage pulses provided between the B+ bus and the B- bus. Thus, the operation of inverter HPI can be controlled by way of a voltage applied to control input terminals CIT1 and CIT2. However, there is a time-constant involved: a voltage applied to terminals CIT1 and CIT2 will charge capacitor C3 by way of resistor R5. With the magnitude of the voltage applied between terminals CIT1 and CIT2 being about 40 Volts, it takes approximately 50 milli-second for capacitor C3 to reach a voltage high enough to cause Diac D3 to break down. 
     As soon as Diac D3 breaks down, base current is provided to control transistor Qc; which therefore starts conducting and thereby preventing capacitor C2 from charging up--thereby, in turn, preventing inverter HPI from being triggered. Even if the voltage between terminals CIT1 and CIT2 is then immediately removed, current will continue to flow into the base of Qc for some period of time. The length of this period is determined by the capacitance value of capacitor C3 as combined with the effective resistance value of R3 in series with D3. In the preferred embodiment, the length of this time period is approximately 30 seconds. After this time period, the conduction of Diac D3 ceases and base current is removed from Qc, thereby again permitting inverter HPI to be triggered by its triggering circuit R2/C2/D2. 
     The purpose of resistor R5 is that of providing a means for discharging capacitor C3 over a relatively long time period--such as several minutes. Its presence has on1y a minor effect on the 30 seconds time-constant associated with C3/D3/R3. 
     Thus, if a DC voltage of about 40 Volt is applied to terminals CIT1/CIT2 for a period of 50 milli-seconds or so, the high-power inverter becomes disabled; and it then remains disabled for a period of about 30 seconds. Thereafter, it resumes normal operation, which will last until a DC voltage of about 40 Volt is again provided to the CIT1/CIT2 terminals for some 50 milli-seconds. 
     In normal operation, both inverters will provide a relatively high-frequency (30 kHz) squarewave AC voltage 100% amplitude-modulated at a frequency of 120 Hz. 
     By way of transformer T1, the output from low-power inverter LPI is apilied between central terminals CT1a/CT1b, as well as between central terminals CT2a/CT2b. By way of auto-transformer T2, the output from high-power inverter HPI is applied between central terminals CT2b/CT2c. Thus, central terminal CT2b acts as a common conductor for the output from both inverters. 
     With reference to FIG. 2, it is seen that central terminals CT1a/CT1b (CT1) and CT2a/CT2b/CT2c/CT2d/CT2e (CT2) are connected with distribution conductor means DCM1 and DCM2, respectively; and, by way of these distribution conductor means, each and every one of the plurality of lamp-ballast assemblies is connected with these central terminals. 
     With reference to FIG. 3, it is noted that--by way of an isolating voltage transformer (ex: CTm1)--the voltage provided from central terminals CT1a/CT1b is used for heating two of the cathodes of the two fluorescent lamps in each lamp-ballast assembly. 
     Also, by way of a small capacitor (ex: Cm1), the voltage from central terminal CT1a is applied to the two connected cathodes (ex: LCm1&#39;/LCm1&#34;)--the purpose being that of aiding in the starting of the fluorescent lamps. (Since the frequency of inverter LPI is not exactly the same as that of inverter HPI, the phasing of the squarewave voltage across central terminals CT1a and CT1b varies in relationship to that of the squarewave voltage across central terminals CT2b and CT2c; which implies that, at least during part of the time, the voltage provided by distribution conductor means DCM1 adds to the voltage provided by distribution conductor means DCM2--as far as lamp starting voltage is concerned.) 
     By way of another isolating voltage transformer (ex: CTm2), the voltage provided from central terminals CT2a/CT2b is used for heating the other two cathodes (ex: LCm2&#39;/LCm2&#34;) of the two fluorescent lamps in each lamp-ballast assembly. 
     Thus, the two lamps (ex: FLm&#39;/FLm&#34;) in each lamp-ballast assembly are series-connected; and these series-connected lamps are connected in parallel with a capacitor (ex: Cm) to form a lamp-capacitor parallel-combination, which parallel-combination is connected in series with an inductor (ex: Lm) to form an overall series-tuned L-C circuit connected between those two of the lamp-ballast assembly&#39;s input terminals (ex: Tm2b/Tm2c) that are connected with central terminals CT2b and CT2c. Thus, this series-tuned L-C circuit being resonant at or near the fundamental frequency of the squarewave voltage provided between central terminals CT2b and CT2c, the overall arrangement provides for resonant ballasting wherein the resonant circuit is series-excited and parallel-loaded. 
     Both the capacitor and the inductor have relatively high Q-factors; which implies that there will be a substantial Q-multiplication effect. That is, absent any loading, the magnitude of the voltage developing across the capacitor will be larger by a factor of Q in comparison to the magnitude of the voltage applied to the series-resonant circuit. Since the net un1oaded Q-factor of the L-C circuit in the preferred embodiment is over 100, the magnitude of the voltage developing across the capacitor--assuming linear operation and no break-down--would reach 12,000 Volt with an input of 120 Volt. 
     However, the L-C circuit is loaded both by the two seriesconnected fluorescent lamps and the Varistor--the Varistor being in effect connected in parallel with the two series-connected lamps. 
     The clamping voltage of the Varistor is so chosen that--in the absence of the fluorescent lamps--the magnitude of the voltage developing across the capacitor is just right for proper rapid-starting of the two series-connected lamps. 
     With the Varistor chosen so as to clamp the voltage across the capacitor to a magnitude suitable for rapid-starting of the series-connected lamps, substantially no current will flow through the Varistor after the lamps have started. Moreover, the lamps will not start if the cathodes are non-incandescent. 
     Thus, when the lamps&#39; cathodes are fully incandescent, the lamps will rapid-start in a matter of a few milli-seconds. However, due to the voltage-magnitude-limiting provided by the Varistor, with cold cathodes the lamps won&#39;t start at all. 
     If, in lamp-ballast assembly LBAm, for some reason the lamps should not start--perhaps because their cathodes had not yet reached incandescence, or perhaps because they were damaged, worn out, or otherwise inoperative, or perhaps because they were disconnected--Varistor Vm will conduct; and current will then flow through the primary winding of current transformer CTm. As a result, a 30 kHz voltage is developed across resistor Rm2; which voltage is rectified by diode Dm2, and the resulting unidirectional voltage is filtered by capacitor Cm2 and provided across terminals Tm2d and Tm2e, and thereby across central terminals CT2d and CT2e. The magnitude of this unidirectional voltage is about 40 Volt. 
     Operation of the Complete System 
     With reference to FIG. 1 and FIG. 3, the complete system of FIG. 2 operates as follows. 
     (a) Upon initial application of power from the power line, inverter LPI immediately commences operation, thereby immediately starting to provide heating power to all the cathodes of all the fluorescent lamps in all of the plural lamp-ballast assemblies. Thus, within about 1.5 second after this initial application of power, all the lamp cathodes are incandescent. 
     (b) About 1.5 second after initial application of power from the power line, inverter HPI commences operation, thereby providing operating power to all the fluorescent lamps. Since by now all the lamps have incandescent cathodes, lamp starting will take place within a few milli-seconds. 
     (c) During the few milli-seconds before the lamps start, the L-C series-resonant ballasting circuits are each loaded with a Varistor, thereby preventing destructive over-voltages. While the Varistors are acting as loads, a DC control voltage of about 40 Volt magnitude is provided between control input terminals CIT1/CIT2. This voltage disappears as soon as the last pair of lamps start; which, under normal circumstances, will be well within 50 milli-seconds. 
     (d) However, if--in one or more of the lamp-ballast assemblies--a pair of lamps should not start within about 50 milli-seconds, the 40 Volt DC voltage provided between control input terminals CIT1/CIT2 will cause inverter HPI to cease operation, thereby removing power from all the series-resonant L-C ballasting circuits. 
     (e) At this point it should be noted that a Varistor--although it can absorb a very large amount of power for a brief period of time--can on1y absorb a miniscule amount of power on an average basis: a large-capacity Varistor is typically rated at about 1 Watt average power, although it may have a rating of more than 100 Joule in terms of energy-absorbing capacity. Thus, in subject system, a Varistor will indeed be able for 50 milli-second or so to safely absorb the approximately 400 Watt or power dissipation it is subjected to in case a pair of lamps fails to start--thereby absorbing a total amount of energy of about 20 Joule. However, within a maximum average power dissipation of 1 Watt, it would not be able to absorb such an amount of energy more often than once every 20 seconds. 
     (f) Due to the resonant nature of the ballasting circuits, the current flowing into each lamp-ballast combination will be substantially sinusoidal in waveshape even though the driving voltage is a squarewave. 
     (g) The fundamental nature of a high-Q resonant series-excited L-C circuit that is parallel-loaded with a gas discharge lamp, is one of providing this lamp with current from the near-equivalent of an ideal current source, with the magnitude of the current provided to the lamp being roughly proportional to the magnitude of the driving voltage, and the magnitude of the power being provided to the lamp being roughly proportional to the magnitude of the voltage present across the lamp. 
     As an overall result, the RMS magnitude of the current drawn from central power supply CPS by the plurality of lamp-ballast assemblies will be roughly proportional to the RMS magnitude of the squarewave voltage provided by this central power supply; which, since this squarewave voltage is amplitude-modulated in direct proportion to the instantaneous magnitude of the DC voltage provided from the full wave rectifier, implies that the magnitude of the instantaneous current drawn by the central power supply from the power line will be roughly proportional to the instantaneous magnitude of the voltage provided therefrom. Thus, the power factor by which the central power supply draws power from the power line will be high--approaching 100%. 
     (h) The amount of power that has to be provided by the low-power inverter LPI is less than 10% of the amount of power that has to be provided by high-power inverter HPI. 
     (i) The fluorescent lamps are started in a particularly gentle rapid-start fashion: the cathodes are allowed to reach full incandescence before lamp operating voltage is applied; and lamp starting aid is provided both by way of a starting capacitor (ex: Cm1 in FIG. 3) and by way of providing a ground-plane next to each lamp. (The ground-plane is not shown, but is indeed present by way of a grounded reflector means mounted directly behind all the lamps.) 
     (j) For extra high power levels, it would be advantageous to use a full-bridge arrangement (instead of the half-bridge arrangement shown) for high-power inverter HPI. That way, 30 kHz/120 Volt would be provided directly from the inverter--without any need for using a voltage transformer at the output. 
     (k) Because the lamp supply voltage is removed within a few milli-seconds if a fluorescent lamp is disconnected from the circuit, the lamp-ballast arrangement of FIG. 3 exhibits a high degree of safety from electric shock hazard. 
     Additional Comments 
     Otherwise, the following points should be noted. 
     (l) Capacitors Ca and Cb of FIG. 1 are sized such as not to store a significant amount of energy in comparison to the amount of energy drawn by the central power supply during one complete half-cycle of the 120 Volt/60Hz power line voltage, while at the same time to store an amount of energy that is several times as large as the amount of energy used by the inverters during one half-cycle of the 30 kHz inverter output voltage. 
     (m) Extra high operating efficiency can be achieved by removing the externally supplied cathode heating power once the lamps have started. This may be simply accomplished by disabling low-power inverter LPI as soon as high-power inverter HPI commences operation. 
     (n) The power supplied to the fluorescent lamps depends on the timing or phasing of the trigger pulses provided to highpower inverter HPI. In turn, the timing of these trigger pulses depend on the delay associated with the process of charging capacitor C2 to a voltage high enough to cause breakdown of Diac D2. The length of this delay can be adjusted over a wide range by adjusting the resistance value of R2. 
     (o) Instead of using two separate inverters (ex: LPI and HPI), a single inverter may be used--with switch means operable to provide the requisite delay in applying the 30 kHz/l20 Volt operating power to the lamps. 
     (p) It is believed that the present invention and its several attendant advantages and features will be understood from the preceeding description. However, without departing from the spirit of the invention, changes may be made in its form and in the construction and interrelationships of its component parts, the form herein presented merely representing the presently preferred embodiment.