Abstract:
A method for maintaining signal integrity of a differential output signal generated from a differential driver is disclosed. The method includes receiving the differential output signal from the differential driver. Once received, the method includes tuning the differential output signal by exposing the differential output signal to an inductance. The inductance is configured to reduce signal mismatch between complementary signals of the differential output signal. The signal mismatch is a result of having each of the complementary signals exposed to different capacitive loading. A device and system is also provided, which include integrating an inductor between the output leads of a differential driver. The inductor is sized for the particular frequency of operation, and the inductor provides an inductance that assists in eliminating mismatch between the complementary signals of the differential output. A reduction and/or elimination of the mismatch will assist in improving the rise-time of the differential signals.

Description:
BACKGROUND OF THE INVENTION  
       [0001]     1. Field of the Invention  
         [0002]     This invention relates generally to methods and structures for improving signal transmission in electronic circuits, and more particularly to methods and structures that enable improvements in rise-time performance for differential output signals.  
         [0003]     2. Description of the Related Art  
         [0004]     In the design and fabrication of electronic circuits, it is well known that capacitive loading, particularly impedance from parasitic capacitance from electrostatic discharge (ESD) protection circuitry, degrades the signal that is being transmitted on conductive traces or leads. As signals are transmitted on conductive leads separated by dielectric materials in a circuit (for example, a circuit fabricated on a multi-layered semiconductor chip), the signals are impeded by parasitic capacitance from the conductive leads. Also, electronic circuits may be subjected to ESD events by simple human handling. As is well known, ESD protection circuitry is designed to direct charge (i.e., current) from an ESD event away from more sensitive circuit elements to a power rail. However, as with any electronic component, ESD protection circuitry has some amount of intrinsic capacitance, which can impede signal transmission.  
         [0005]     For signal transmission, it is particularly important, especially at higher frequencies (e.g., &gt;1 GHz), to maintain good signal integrity. Although capacitive loading is a problem in single-ended data transmission, the problem can be exacerbated when driving differential signals. This is particularly true when a mismatch in capacitive loading is present at a pair of complementary output leads. In this situation, the differential output signal can be significantly degraded since each output leas may be subjected to a different amount of capacitive loading, which causes the output lead to have different slew rates and thus introduce mismatch into the switching behavior of the differential signal. However, even if the capacitive loading is matched, the presence of excessive capacitive loading can still substantially degrade differential signal transmission by slowing down its switching behavior, i.e. increases its low to high slew rate and its high to low slew rate.  
         [0006]     As well known in the art, any circuit component has some amount of intrinsic, parasitic, capacitance. Therefore, minimizing capacitive loading along a signal path can be difficult since the signal path itself is a source of capacitive loading. Typically, reducing the size of components that are coupled to a signal path minimizes intrinsic capacitive loads. However, the size of certain circuit components cannot be reduced. For example, ESD protection circuits, which must withstand high voltages, and quickly discharge large current spikes, are generally large and must be attached to input and output pads to protect the integrated circuit (IC). Furthermore, although advances in IC manufacturing has led to reduction of device sizes, the size of ESD circuitry has not followed the same reduction because the amount of charge ESD circuitry must withstand has not seen a reduction. Thus, the size of ESD circuitry has remained relatively unchanged, while other circuit components have been reduced. As a result, ESD protection circuitry will generally add a substantial amount of intrinsic capacitive loading at an output, such as an output signal driver. As an example, at high operating frequencies, such as of 1.25 GHz, ESD protection circuitry should not present capacitive loading greater than 0.8 pF, otherwise the signal from an output driver may be degraded.  
         [0007]     In order to minimize this potential problem in high frequency devices, circuit designers have typically designed impedance matching devices to null-out load impedance presented by ESD circuitry, pad capacitance, etc., and ultimately, provide matched output load impedance. Matched load impedance provides an environment where signal integrity can be maintained.  
         [0008]      FIG. 1  illustrates a typical impedance matching technique  100  that provides independent and separate impedance matching networks  110   a  and  110   b  respectively on output leads  108   a  and  108   b  of a differential driver  106 . As illustrated in  FIG. 1 , the differential driver  106  receives complementary signals Din and Din_c on leads  104   a  and  104   b  from core circuitry  102 . The differential driver  106  produces complementary signals Din′ and Din_c′ on output leads  108   a  and  108   b.  To protect the differential driver  106  and core circuitry  102  from ESD events, separate ESD protection circuitry, represented by their effective capacitive loads  112   a  and  112   b,  are respectively connected to the first and second output leads  108   a  and  108   b.  Each component of the differential output signal carried on the differential output leads  108   a  and  108   b  is independently and separately matched to compensate for capacitive loading from parasitic capacitance and each of the effective capacitive loads  112   a  and  112   b.  Unfortunately, implementing the impedance matching networks  110   a  and  110   b  on-chip requires significant silicon area for their integration. Another drawback of implementing impedance matching networks  110   a  and  110   b  is the potential for mismatch between matching networks due to process variations in the IC fabrication process. Consequently, because each impedance matching network  110   a  and  110   b  is independently matched, mismatch will still happen between the signals output from the output leads  108   a  and  108   b.    
         [0009]     U.S. Pat. Nos. 6,278,339 and 6,249,193 are directed to methods of impedance matching in single-ended drivers by incorporating an adjustable-length transmission line. The transmission line is adjusted in proportion to the magnitude of transients on the driver circuit output. Parallel conductive lines are formed on a printed circuit board, PCB, and shorted by a movable stub from the transmission line.  
         [0010]     Another technique for single-ended driver output matching is set forth in U.S. Pat. No. 6,509,755. This patent disclosed a method of detecting an output current from the driver to the load, and scaling the detected current. The scaled current is then subtracted from the input voltage level, thereby providing a dynamic impedance matching technique.  
         [0011]     Also, U.S. Pat. No. 6,522,083 proposed a method of tuning the driver output by using an isolation circuit and matching network coupled to the output driver.  
         [0012]     These patents provide ways for individual impedance matching in single ended driver outputs and thus fail to address the potential for mismatch between each of the outputs of a pair of differential outputs. Thus, there is a need for methods and structures that provide improved matching for output signals, and particularly those signals that are driven off chip.  
       OBJECTS OF THE INVENTION  
       [0013]     One object of the present invention is to provide a structure and method for reducing impedance load effects.  
         [0014]     Another object of the present invention is to provide a structure that can be incorporated in an IC.  
         [0015]     A further object of the present invention is to provide a structure that can easily be modified to counteract the impedance load effects of various load structures having differently sized parasitic capacitances.  
         [0016]     Yet another object of the present invention is to provide a structure and method that provides better matching of the upward and downward slew rates of the complementary outputs of a differential output signal, such that signal integrity can be maintained.  
       SUMMARY OF THE INVENTION  
       [0017]     The present invention provides the methods and structures that enable improvements in rise-time performance and reduce signal mismatch in differential output signals. As used herein, “signal mismatch” in differential signals is a condition that occurs when simultaneously outputted signals of a differential signal pair, which are 180 degrees output of phase relative to each other, have different rise and fall times, i.e. slew rates, such that the upward swinging output signal reaches a logic high voltage level much before or much after the downward swinging output signal reaches a logic low voltage level. Thus, even though a differential signal output pair has one output signal going high and one output signal going low, a mismatch happens when the signal going low is not lined up (e.g., is offset, slower, faster, etc), with the signal going high of the same differential signal output pair. Several inventive embodiments of the present invention are described below.  
         [0018]     In one embodiment, a method for maintaining signal integrity of a differential output signal generated from a differential driver is disclosed. The method initially includes receiving the differential output signal from the differential driver. Then, tuning the differential output signal by exposing the differential output signal to an inductance. The inductance is configured to reduce signal mismatch between complementary signals of the differential output signal, where the signal mismatch is a result of having the complementary signals exposed to different capacitive loading.  
         [0019]     In another embodiment, a tuning circuit for improving rise-time of a differential output signal is provided. The tuning circuit includes a differential driver for receiving a differential input and generating a differential output signal onto a first differential output lead and a second differential output lead. Further included is an inductor coupled between the first differential output lead and the second differential output lead of the differential driver. First electrostatic discharge (ESD) capacitive circuitry is coupled to a first output terminal. The first output terminal is coupled to the inductor, and second ESD capacitive circuitry is coupled to a second output terminal, where the second output terminal is coupled to the_inductor. The inductor is positioned between the differential driver and the first output terminal and the second output terminal. In this embodiment, the inductor produces an inductance between the first differential output lead and the second differential output lead, and the inductance acts to reduce signal mismatch in complementary signals of the differential output signal that is to be presented to the first and second output terminals.  
         [0020]     In yet another embodiment, a tuning device for improving rise-time of a differential output signal generated in a semiconductor chip is provided. The tuning device includes core circuitry and a differential driver. The differential driver interfaces with the core circuitry and is capable of receiving a differential input from the core circuitry. The differential driver is configured to produce a differential output signal onto a first differential output lead and a second differential output lead. Further included is an inductor that is coupled between the first differential output lead and the second differential output lead of the differential driver. Also part of the tuning device is first electrostatic discharge (ESD) circuitry that is coupled to the first differential output lead which connects to a first pad and the inductor. Second ESD circuitry is coupled to the second differential output lead that connects to a second pad and the inductor. The inductor is capable of producing an inductance between the first differential output lead and the second differential output lead, and the inductance acts to reduce signal mismatch in complementary signals of the differential output signal that is to be presented to the first pad and the second pad.  
         [0021]     In still another embodiment, a tuning system for improving rise-time of a differential output signal generated in a semiconductor chip is disclosed. The system includes core circuitry and a differential driver. The differential driver interfaces with the core circuitry and is capable of receiving a differential input from the core circuitry. The differential driver is configured to produce a differential output signal onto a first differential output lead and a second differential output lead. The system further includes first electrostatic discharge (ESD) circuitry that is coupled to the first differential output lead that connects to a first pad, and a second ESD capacitive structure that is coupled to the second differential output lead that connects to a second pad. The system also includes an off-chip inductor. The off-chip inductor is interconnected to the first pad and the second pad, and the off-chip inductor produces an inductance between the first pad and the second pad, where the inductance acts to reduce signal mismatch in complementary signals of the differential output signal that is to be presented to the first pad and the second pad.  
         [0022]     In another embodiment, an integrated circuit is provided. The integrated circuit is capable of outputting a differential output signal. The integrated circuit includes a differential driver for receiving a differential input and generating a differential output signal onto a first differential output lead and a second differential output lead. The integrated circuit also includes an inductor that is coupled between the first differential output lead and the second differential output lead of the differential driver. Further included is first electrostatic discharge (ESD) capacitive circuitry that is coupled to a first output terminal, and the first output terminal is coupled to the inductor. Second ESD capacitive circuitry is coupled to a second output terminal, and the second output terminal is coupled to the_inductor. The inductor is positioned between the differential driver and the first output terminal and the second output terminal. The inductor produces an inductance between the first differential output lead and the second differential output lead, wherein the inductance acts to reduce signal mismatch in complementary signals of the differential output signal that is to be presented to the first and second output terminals.  
         [0023]     In one embodiment, a system for maintaining signal integrity of a differential output signal generated by a differential driver is disclosed. The system includes means for receiving the differential output signal from the differential driver. The system also includes means for tuning the differential output signal by exposing the differential output signal to an inductance. The inductance is configured to reduce signal mismatch between complementary signals of the differential output signal, where the signal mismatch is a result of having the complementary signals exposed to different capacitive loading.  
         [0024]     Other aspects and advantages of the invention will become apparent from the following detailed description, taken in conjunction with accompanying drawings, illustrating by way of examples the principles of the invention.  
     
    
     BRIEF DESCRIPTION OF THE DRAWINGS  
       [0025]     The present invention will be readily understood by the following detailed description in conjunction with the accompanying drawings, where like reference numerals designate like structural elements.  
         [0026]      FIG. 1  is a schematic diagram showing a typical load impedance technique where independent and separate impedance matching networks are used.  
         [0027]      FIG. 2A  is a block diagram of a first embodiment of the present invention as applied to a single-ended output driver.  
         [0028]      FIG. 2B  is a schematic diagram of a cross-coupled signal matching technique where a cross-coupled inductor is used to tune a differential output signal, in accordance with a second embodiment of the present invention.  
         [0029]      FIG. 3A  is a diagram of a partially exposed semiconductor chip showing where an inductor is used to reduce or substantially eliminate mismatch of a differential output signal, in accordance with one embodiment of the present invention.  
         [0030]      FIG. 3B  is a diagram a partial view of a semiconductor chip showing an alternative method of implementing inductance to reduce or substantially eliminate mismatch of a differential output signal, in accordance with an embodiment of the present invention.  
         [0031]      FIG. 3C  is a diagram of a partial view of a semiconductor chip showing another method of implementing inductance to reduce or substantially eliminate mismatch of a differential output signal, in accordance with an embodiment of the present invention.  
         [0032]      FIG. 3D  is a diagram a semiconductor chip on a printed circuit board showing a discrete off-chip inductor being used to reduce or substantially eliminate mismatch of a differential output signal in accordance with an embodiment of the present invention.  
         [0033]      FIG. 4  is a graph of signal pulses illustrating the improvements in rise-times of one output lead of a differential output driver signal as the applied inductance is varied, in accordance with an embodiment of the present invention.  
     
    
     DETAILED DESCRIPTION  
       [0034]     The present invention, as illustrated by the following embodiments, provides the methods and structures that enable improvements in rise-time performance for single ended outputs, and improvements in rise and fall times for differential output signals. In particular, differential output signals that need to be driven off-chip will benefit from the improvements in rise and fall time performance. As should be appreciated, the present invention can be implemented in various ways, including a method, system, or device. In some instances, well known process operations have not been described in detail in order to avoid obscuring the present invention.  
         [0035]     With reference to  FIG. 2A , a differential driver  101  is typically comprised of two single-ended drivers  100   a  and  100   b,  each having separate outputs D+ and D− for driving respective output leads  108   a  and  108   b.  Each driver  100   a  and  100   b  drives the complementary signal of the other. That is, while driver  100   a  outputs a true signal on output D+, driver  100   b  drives the complement signal on output D−, and vise-versa. For the sake of simplicity, the following discussion regarding  FIG. 2A  describes the present invention as individually, and separately, applied to each single-ended driver  100   a  and  100   b.  Later, a description of the present invention simultaneously applied to both outputs D+ and D− of differential driver  101  is given. It is to be understood that much of the invention description given here as individually applied to a single-ended driver,  100   a  or  100   b,  may be applied to the present invention simultaneously applied to both outputs D+ and D− of a differential output driver  101 .  
         [0036]     Each output D+ and D− of a differential output driver  101  typically includes electrostatic discharge (ESD) protection circuitry to clamp to VCC any upward voltage surges and clamp to ground any downward voltage surges. Minimally, an ESD circuit may consist of a single clamping diode between an output lead and a power rail, VCC or ground. However, various types of ESD circuitry are known, and for the sake of brevity, only the parasitic capacitance CESD intrinsic to all ESD circuitry is shown.  
         [0037]     Irrespective of their specific circuit configuration, all ESD circuits need to react quickly, withstand very high voltages, and sink large currents. Therefore, ESD circuitry is typically large, and thus adds a significant amount of parasitic capacitance CESD to an output driver  100   a  or  100   b.  The relative large size of the ESD circuitry is especially pronounced when compared with the miniaturized circuitry of the internal core of an IC, which the ESD circuits protect. This disparity in size is exacerbated as advances in IC manufacturing further reduce the minimum device size of the core circuitry since the size of ESD circuits cannot be reduced along with the core circuitry due to the magnitudes of electrostatic discharge an IC must withstand (i.e. static electricity from a handler) remaining unchanged. Therefore, the relative size of ESD circuitry, and thereby the relative size of its intrinsic parasitic capacitance (as compared to the core circuitry) increases as the minimum device size of the core circuitry is reduced. This poses a growing problem since a smaller device has a reduced capacity for driving current, and it therefore requires more time to charge the ESD circuit&#39;s parasitic capacitance in order to bring an output signal high and requires more time to discharges the ESD&#39;s circuit&#39;s parasitic capacitance in order to bring an output signal low. Consequently, more time is traditionally required to drive outputs having ESD protection circuitry, or other circuits having large intrinsic capacitances. This limitation in speed performance is exacerbated at high frequency requirements since the necessity for ESD circuitry can significantly limit the output driver&#39;s maximum operating frequency.  
         [0038]     As it is known, the larger a capacitive load, the more time it takes to raise or lower a voltage potential across it. This time period may be reduced by increasing the amount of driving current, but this requires increasing the size each output driver  100   a  and  100   b,  and thus increasing the cost of an IC. Additional problems arise in differential output driver circuitry  101  since they require that their two outputs D+ and D− have exact opposite swings, but mismatch in the amount of load capacitance  112   a  and  112   b  at each differential output lead  108   a  and  108   b  can result in a different time constant for each, and thereby result in different voltage swings. As result, each of the two outputs D+ and D− of a differential output driver  101  may have a different time constant resulting in a mismatch in their opposite voltage swings (i.e. each of the two outputs would have a different rise and fall times).  
         [0039]     Since the above-described problems are more pronounced at higher frequencies, the present invention seeks to reduce the capacitive loading effects of circuits (such as ESD circuitry) at the output of a signal driver.  
         [0040]     An output driver in accord with the present invention adds a compensating inductance in parallel with the parasitic capacitance CESD of the EDS circuit at each output D+ and D 1 . For example, inductance La is placed in parallel with parasitic capacitance  112   a  and inductance Lb is placed in parallel with parasitic capacitance  112   b.  This creates an effective bandpass frequency filter  51   a  and  51   b  at each output D+ and D− of each driver  100   a  and  100   b.  When designing an output driver for a high frequency application, one typically knows the frequency range at which the output driver is expected to operate. Since the desired operating frequency of each output driver  100   a  and  100   b  is known, the inductive values of La and Lb can be selected such that when each is combined with its corresponding parasitic capacitance  112   a  and  112   b,  the parallel combination creates a bandpass filter ( 51   a  and  51   b ) having resonance at the desired operation frequency. Thus, when individually applied to a single-ended driver, the operation of the present invention is dependent on frequency. Therefore, the when applied to a single-ended output driver, the present invention may be particularly suited for use with circuits having sustained operation at a particular frequency, such as the output of a clock generator, or oscillator.  
         [0041]     Although the use of an inductor to nullify the loading effects of parasitic capacitance CESD addresses the problem of improving the maximum operating frequency of an output driver, applying a separate inductance La and Lb to each output lead  108   a  and  108   b  of a differential output driver does not address the issue of signal mismatch. That is, inductances La and Lb, which may be implemented using discrete or integrated inductors, may themselves not be perfectly matched and may themselves add some amount of mismatched intrinsic capacitance. This problem is solved in the structure of  FIG. 2   b,  where inductors La and Lb are replaced with one cross-coupled inductor  210 . This eliminates any additional mismatch due to using different inductors La and Lb, and since the two outputs of the differential output drivers have opposite voltage swings, the configuration is suitable for general differential signal drivers and is not limited to clock applications.  
         [0042]      FIG. 2B  illustrates a cross-coupled signal matching technique  200  in accordance with one embodiment of the present invention. Differential driver  206  receives a differential signal from a first differential input lead  204   a  and a second differential input lead  204   b  produced by core circuitry  202 . In turn, the differential driver  206  produces a differential output signal on a first differential output lead  208   a  and a second differential output lead  208   b.  The differential driver  206  and the core circuitry  202  are protected from electrostatic discharge, ESD, events by first ESC protection circuitry represented by effective capacitive load  212   a  and second ESD protection circuitry represented by effective capacitive load  212   b.  Hereinafter, ESC protection circuitry will be represented by its respective effective capacitive load. The effective capacitive loads  212   a  and  212   b  are respectively connected to the first and second differential output leads  208   a  and  208   b,  and a first output terminal  214   a  and a second output terminal  214   b.  A cross-coupled inductor  210  is coupled between the first and second differential output leads  208   a  and  208   b.  The cross-coupled inductor  210  provides inductance to simultaneously tune both output signals of the differential output driver on first and second differential output leads  208   a  and  208   b.  Each differential output signal, when produced, will be exposed to the inductance. Consequently, signal mismatch between the two signals of the differential output resulting from capacitive loading is reduced or substantially eliminated. That is, the highs and lows of the complimentary signals of the differential driver are aligned and matched, such that signal integrity is maintained.  
         [0043]     Still referring to  FIG. 2B , in one particular embodiment, the cross-coupled inductor  210  is positioned between the differential driver  206  and the effective capacitive loads  212   a  and  212   b  of the ESD circuitry. The cross-coupled inductor  210  should be sized so as to provide resonant tuning of the ESD load capacitance at a specific maximum frequency of operation with cross-coupled inductor structure connected between the differential output terminals. In yet another embodiment, the cross-coupled inductor  210  can be a configurable inductor, using switch transistors to tap various points of an inductor (or multiple inductors) to adjust the cross-coupled inductance and produce the desired output performance (e.g., waveform) for the two differential output signals on first and second differential output leads  208   a  and  208   b.    
         [0044]     Parasitic capacitance may be determined based on the surface area and material properties of the respective differential output leads  208   a  and  208   b.  Intrinsic parasitic capacitance may also be determined based on the size and inherent properties of the components and isolative layers (e.g., the ESD protection circuitry) that are implemented. In some implementations, parasitic capacitance of the leads and attached components may be measured separately, and in other implementations, their combined parasitic capacitance may be measured as an effective total capacitance. Still further, depending on the target operational frequency, a specifically sized inductor can be integrated into the design. In this manner, the inductance will be appropriately proportioned to handle the anticipated impedance under the pre-set frequency of operation.  
         [0045]     For illustration purposes, the differential output signal can be operated at a frequency of about 1.25 GHz, and the cross-coupled inductor  210  can be sized to produce an inductance between about 10 nH and about 25 nH. This range of inductance can thus tune the differential output signal, and thus reduce or substantially eliminate the mismatch produced by parasitic capacitance introduced by the ESD protection circuitry represented by its respective effective capacitive loads  212   a  and  212   b.  Of course, from chip-to-chip the frequency will be different and the sizing of the inductor  210  will be made according to the chip frequency and anticipated mismatch produced by the imbalance resulting from parasitic capacitive loading.  
         [0046]      FIG. 3A  illustrates a partially exposed semiconductor chip  300 . The partially exposed semiconductor chip  300  illustrates a die  300   z  having core circuitry  202 ′, a differential driver  206 ′, a cross-coupled inductor  210 ′, effective capacitive loads due to ESD circuits  212   a ′ and  212   b ′, and a first pad  304   a  and a second pad  304   b.  First and second bond wires  306   a  and  306   b  are respectively coupled to the first and second pads  304   a  and  304   b  and to output pins (not shown) of the semiconductor chip  300 . In one embodiment of the present invention, the inductor  210 ′ is implemented at a periphery of the semiconductor chip  300 , which is the approximate location at which signals are driven off-chip. In another embodiment, first and second pads  304   a  and  304   b  are input/output pads capable of receiving input signals as well as transmitting output signals.  
         [0047]     Still referring to  FIG. 3A , in one embodiment, inductor  210 ′ is a cross-coupled inductor. Inductor  210 ′ may be fabricated as a multi-leveled structure in the semiconductor chip  300  (such as a multi-chip package structure) or on die  300   z.  Or, the inductor  210 ′ can be fabricated substantially on one layer, and conductive vias and metal traces can complete the interconnections or cross-coupling, depending on the design of the inductor.  
         [0048]      FIG. 3B  illustrates an implementation wherein inductance is provided by a thin wire, in accordance with one embodiment of the present invention. As well known in the art, wires have an inherent amount of inductance. A wire of appropriate size with a desired inductance is selected for semiconductor  300 A, and is coupled to bond wires  306   a  and  306   b  to provide an appropriate amount of inductance to reduce or substantially eliminate the mismatch of the differential signal due to parasitic capacitive loading. This embodiment may be particularly useful for maintaining signal integrity at higher frequencies. Such higher frequencies may be in the range of about 5 Gigahertz or higher.  
         [0049]      FIG. 3C  shows semiconductor  300 B, in accordance with another embodiment of the present invention. Bond wires  306   a  and  306   b  have an inherent amount of inductance, and by coupling bond wires  306   a  and  306   b  at a selected contact point  210   b  at a predetermined distance from bond pads  304   a  and  304   b,  a desirable amount of inductance can be configured to reduce or substantially eliminate the mismatch in the differential signal to maintain signal integrity. This embodiment may be useful at higher frequencies. Such higher frequencies may be in the range of about 5 Gigahertz or higher.  
         [0050]      FIG. 3D  illustrates yet another embodiment where inductance may be provided by a discrete inductor  210   c  implemented outside of the semiconductor chip  300 C. Discrete inductor  210   c  is connected to conductive leads  310   a  and  310   b  on printed circuit board  350 . Output pins  308   a  and  308   b  from semiconductor chip  300 C are connected to the conductive leads  310   a  and  310   b.  Discrete inductor  210   c  is appropriately sized so as to provide the proper amount of inductance to reduce or substantially eliminate the mismatch of the differential signal being output by the semiconductor  300 C. The use of a discrete component on the printed circuit board  350  may be more suited for embodiments that operate at lower frequencies. Such lower frequencies may be those that are lower than about 1 Gigahertz.  
         [0051]      FIG. 4  shows exemplary signal pulses of different rise times dependent on different inductance values used for the inductor  210  (see  FIG. 2A ), in accordance with one embodiment of the present invention. The graph shows plots of rise-times for a differential output signal at a load impedance of 2 pF coupled in parallel with a 100 Ω resistance, as various inductances are applied to the differential output signal. A solid curve, as shown on the rise-time graph  400 , is a plot of rise-time for a differential pulse signal operated at 1.25 GHz. The solid curve is the reference result without providing an inductance in accordance with the embodiments of the invention. The other curves shown on the rise-time graph  400  are plots of rise-times for the differential output signal with various inductances ranging from about 10 nH to about 25 nH applied to the differential signal to tune out the signal mismatch.  
         [0052]     As can be seen on  FIG. 4 , the rise-time of the differential signal is improved as inductance is applied to the output signal lead. However, it should be understood that the inductances, as illustrated in  FIG. 4 , are only example values, and these values will change depending on the circuit arrangement and the frequency of operation. Consequently, the structural implementation of the inductor  210 , which is coupled between the differential output leads  208   a  and  208   b,  can function at a number of frequency ranges and between other signal lines that require impedance mismatch balancing. Thus, the specific inductive value of the inductor  210  will change and should be selected for the specific structural, circuit, and frequency application.  
         [0053]     As described herein, reference was made to an integrated circuit (IC) chip, which implements wire bond leads around the IC chip&#39;s periphery. However, it should be understood that the embodiments of the present invention are equally applicable to alternative chip interconnections. For instance, it is envisioned that instead of wire bond leads, the interconnection can be achieved through flip-chip connections. Such flip-chip connections are sometimes referred to as “bumped” or “c4” conductive connections. Further, flip-chip connections are not limited to placement around the periphery of the IC chip, as the interconnections can be distributed throughout a surface of the IC chip.  
         [0054]     Although the foregoing invention has been described in some detail for purposes of clarity of understanding, it will be apparent that certain changes and modifications may be practiced within the scope of the appended claims. Accordingly, the present embodiments are to be considered as illustrative and not restrictive, and the invention is not to be limited to the details given herein, but may be modified within the scope and equivalents of the appended claims.