Abstract:
A method of connecting signal lines between an integrated circuit (IC) die and a carrier or external circuit, and corresponding apparatus. Techniques for adjusting magnetic coupling between terminated signal lines include splitting a return path for termination current and disposing one nearby on either side of the terminated signal line, creating two small termination current loops conducting in opposite directions; using separate terminating impedances, which may be unequal, to control current in each of the loops; and arranging major axes of the termination current loops for a signal to be perpendicular to those of the isolation-target signal. Capacitive coupling adjustments include routing ground potential termination current return connections nearby the signal connection to shield it from the isolated signal line, using dual overlapping connections to shield each return path, and adjusting dielectric material proximity to the signal paths. For isolation across a limited frequency range, increasing either inductive or capacitive mutual coupling above the achievable minimum may create an isolation null at the desired frequency that effects higher isolation than is obtainable with minimum coupling values.

Description:
CROSS REFERENCE TO RELATED APPLICATIONS 
       [0001]    This application claims the benefit under 35 USC 119 of U.S. Provisional Application identified by attorney docket number PER-017-PROV, Application Ser. No. 60/812,191 filed Jun. 9, 2006 and entitled “Mounting Integrated Circuit Dies for High Frequency Signal Isolation” which is hereby incorporated herein in its entirety by reference. 
     
     BACKGROUND OF THE INVENTION 
       [0002]    1. Field of the Invention 
         [0003]    The disclosed methods and apparatus relate broadly to electronic integrated circuits (“ICs”), and more specifically to interfacing IC dies to circuits in which they are employed. 
         [0004]    2. Related Art 
         [0005]    ICs must generally be connected to external circuitry to be useful, and the interconnection itself may impact the net high frequency performance of the IC. For example,  FIG. 1  illustrates an exemplary SPDT analog switching circuit. A first high frequency signal, RF 1 , is input to pin  3 . A second high frequency signal, RF 2 , is input to pin  13 . Control signals provided between pins  16  or  17  and  19  (GND) determine whether an RF common connection RFC is coupled to RF 1  or to RF 2 . This particular exemplary analog switch provides switchable resistive termination into 75 ohms for any one of the three signal connections (RF 1 , RF 2  or RFC) that is not otherwise properly terminated for RF signals. 
         [0006]    An IC as shown in  FIG. 1  may be employed in electronic devices that have stringent isolation requirements. Such requirements may derive from functional performance needs of the equipment employing the IC. Often, however, isolation requirements between terminals are defined by regulations that have little or nothing to do with adequate performance. Circuits such as the switch illustrated in  FIG. 1  may be subject, for example, to the isolation requirements of FCC Part 15.115. These requirements include, among others, a requirement for isolation of −80 dB between any two of the signal lines RF 1  and RF 2  at a range of frequencies up to 216 MHz. Other regulations, and/or performance requirements, may establish correspondingly different isolation requirements. 
         [0007]    An integrated circuit (IC) alone might satisfy such isolation requirements, yet fail when packaged in a carrier. A carrier typically provides a mounting and protection for an IC, together with terminals that are more readily connected to an external circuit than would be the connections, or pads, on the IC itself. Techniques by which the IC is protected and connected to the carrier may impair the inherent signal isolation provided by the IC alone. The interconnection techniques described herein help to satisfy both performance needs and regulatory requirements by minimizing the degradation of IC signal isolation that may be caused by mounting in a carrier. 
       SUMMARY 
       [0008]    A method of connecting an IC connection pad of a signal line is provided for an integrated circuit (“IC”) that includes a plurality of signal lines, each separately connectable to a common signal line, including a first signal line that is terminated to ground through a termination network when the first signal line is not connected to the common signal line. The method maintains high isolation of the terminated first signal line with respect to an isolation-target signal line by techniques that include splitting the signal line termination current so that it returns via a plurality of first signal return pads disposed on different sides of the first signal IC connection pad and separately connected to a common or ground connection on the carrier. The termination current thus divides between a plurality of first signal return paths, which creates opposing current loops to reduce inductive flux coupling to the isolation-target signal line (e.g., a second signal line, or the common signal line with respect to which high isolation is required). The area of the opposed termination current loops may be adjusted for best cancellation of magnetic flux with respect to the isolation-target signal connection. The return path connections (e.g., bond wires) from the first signal return pads may be connected to a ground plane of the carrier at corresponding plane connection points. Moreover, the current in the opposed current loops may be made unequal by employing different termination impedances for the different termination current loops. 
         [0009]    The IC interconnection method may include, either alternatively or additionally, disposing conductors at a ground or AC common potential between the first signal line connection and the isolation-target signal line connections to reduce capacitive coupling. In the case where the return path connections from the first signal return pads are made to a carrier ground plane, this may include connecting the return conductors on the ground plane at points more distant from the IC die than a point of connection of a conductor from the ground plane to a corresponding carrier return terminal. Further, when two conductor wires are used for each return path, each may be connected to the carrier ground plane about as far from their other terminus as possible while remaining quite near the signal wire, so that they each provide ground potential shielding for the connection wire. 
         [0010]    A method of configuring connections between a signal switching integrated circuit (IC) die and external circuit terminals is also disclosed. The signal lines include a first signal line, a first signal termination return line, an isolation-target signal line, and an isolation-target termination return line. The method enhances isolation between the first signal line and the isolation-target signal line at a particular frequency when the first signal line is terminated by a terminating impedance coupled between the first signal line and a corresponding termination current return connection. For each of the first signal line and the isolation-target signal line, this method includes splitting the return termination current so that it is conducted via a plurality of return current paths that are established adjacent to and on opposite sides of a path connecting the corresponding signal line between the IC die and the external terminal. The method further includes adjusting capacitive coupling between the first signal line and the isolation target signal line in accordance with any technique as described in more detail below; and adjusting magnetic coupling between the first signal connection and the isolation target signal connection in accordance with any technique described in more detail below, such that the mutual capacitive and magnetic couplings interact to provide an isolation between the signal lines that is higher, at a target frequency subject to stringent isolation requirements, than would be due to either the mutual capacitive coupling alone or the mutual magnetic coupling alone at such target frequency. Each method set forth hereinbelow for changing mutual capacitive coupling between the signal lines, and each method set forth for changing mutual magnetic coupling between the signal lines, and each functional combination of such method, is combined with the configuring method set forth above to create a different embodiment of this method. 
         [0011]    Additional aspects include any apparatus that a skilled person would understand, in view of the description set forth below, as being configurable to implement any of the methods described above. 
     
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         [0012]    Embodiments of the present invention will be more readily understood by reference to the following figures, in which like reference numbers and designations indicate like elements. 
           [0013]      FIG. 1  is a simplified illustration of a high frequency analog switch integrated circuit disposed in a carrier package, with signal paths schematically represented. 
           [0014]      FIGS. 2A ,  2 B,  2 C and  2 D schematically represent termination current path configurations;  2 A is prior art, while  2 B,  2 C and  2 D show alternative configurations. 
           [0015]      FIG. 3  illustrates an early IC/carrier interconnection configuration. 
           [0016]      FIG. 4  illustrates a first alternative IC/carrier interconnection configuration. 
           [0017]      FIG. 5  illustrates a second alternative IC/carrier interconnection configuration. 
           [0018]      FIG. 6  illustrates a third alternative IC/carrier interconnection configuration. 
           [0019]      FIG. 7  is a graph illustrating interactions between quantities of mutual magnetic coupling and quantities of mutual capacitive coupling that are arranged to exist between signal lines to be isolated. 
       
    
    
     DETAILED DESCRIPTION 
       [0020]      FIG. 1  illustrates, in a simplified quasi-schematic manner, signal switching functionality for an exemplary integrated circuit (IC) die  102  that is mounted on an IC package or carrier  104 . The carrier  104  includes terminals used for connecting the IC to a circuit in which it is employed. In particular, a first RF signal will be connected to a terminal  106  that is labeled “RF 1 ” and indicated as pin “ 3 .” A second RF signal will be connected to a terminal  108  (RF 2 ,  13 ). An RF common will be connected to a terminal  110  (RFC,  8 ). 
         [0021]    Each of the RF signal terminals is connected to the IC die  102 , which includes switches to connect the signal to either an RF common, or to a termination path. The first RF signal, for example, is typically coupled to a terminating impedance  112  (here, 75 ohms resistive) via a first signal termination switch  114  when a first signal switch  116  is open (so that the signal is not terminated by another circuit). The second RF signal is shown similarly disconnected from other circuitry by an open second signal switch  118 , and accordingly is connected to a terminating impedance  120  via a second signal terminating switch  122 . 
         [0022]    Because the RF common signal is not connected to either the first or second RF signals, the RF common signal is generally therefore connected to a terminating impedance  124  via a common termination switch  126 , as shown. When either of the RF signals is connected to the RF common, the corresponding RF signal termination switch is typically opened. 75 ohm resistive terminating impedances are shown in this example, but the impedance may be set to any appropriate value. The terminating impedance will typically be set to the expected characteristic impedance of the transmission lines that connect the various RF signals to the IC. 
         [0023]      FIGS. 2A-2D  illustrate various circuit configurations by which a termination path, including appropriate terminating impedance elements, may be coupled between a signal pad  202  of the IC die (e.g., the IC pad for the first RF signal) and one or more signal return pads  204 ,  206 .  FIG. 2A  represents a typical prior art configuration, in which an appropriate terminating impedance  208  may be coupled between the signal pad  202  and a return pad  204  via a termination switch  210 .  FIG. 2B  is similar, except that a second return pad  206  is connected to the first return pad, and is disposed on roughly the opposite side of the signal pad  202  such that oppositely-directed return current loops may be created. The termination switch  210  and the terminating impedance  208  is shown to be configured as in  FIG. 2A . 
         [0024]    In  FIG. 2C , two signal return pads  204  and  206  are again disposed on either side of the signal pad  202 .  FIG. 2C , however, includes separate terminating impedance elements  212  and  214  to control the current flow from the signal pad  202  to the signal return pads  204  and  206 , respectively. In some situations, the two corresponding switches  216  and  218  may be employed for circuit layout convenience. However, the switches  216  and  218  are typically either both on or both off at any given time. Consequently, a single switch would suffice for this purpose if the layout permits. Because the signal return pads  204  and  206  are expected to be connected to the same potential, generally ground, in operation, the two 150 ohm impedance elements should be effectively in parallel to yield the same 75 ohm net terminating impedance as in  FIGS. 2A and 2B . 
         [0025]    The physical and circuit layout represented by  FIG. 2D  is the same as for  FIG. 2C , except that the two terminating impedance elements  212  and  214  have been made unequal, to 169 and 135 ohms, respectively. Other values will be selected as appropriate for particular embodiments to minimize coupling between the RF signal connected to the signal pad  202  and an isolation-target signal that is connected elsewhere on the IC. It may be useful to dispose the larger impedance element  212  in a return path that is physically closer to the signal pad of the isolation-target signal than is the other return path. Alternative or additional techniques may be used to minimize the magnetic mutual coupling between the RF signal and the isolation-target signal. For example, the net loop area for the closer signal return path may be made smaller, or may be made more orthogonal to the effective loop area of the isolation-target signal. 
         [0026]      FIG. 3  illustrates features of connections between an exemplary IC carrier  302  and an IC die  304  mounted thereupon. This exemplary carrier includes a conductive plane area  306  of the carrier  302 , upon which the IC  304  is physically attached, and twenty terminals, numbered 1-20, disposed about the perimeter of the carrier  302 . In this older configuration, a bond wire  308  connects the first signal pad on the IC  304  to a first signal terminal # 3   310 . Another bond wire  312  connects a first signal return pad on the IC to a first signal return terminal # 4   314 . The second RF signal and return pads are similarly connected to a second signal terminal # 13   318  and a second signal return terminal  320 , respectively. 
         [0027]    A bond wire  322  connects the RF common signal pad to an RF common signal terminal # 8   324 . For symmetry with the signal connections between which it is disposed, the RF common signal termination path is arranged in the manner shown in  FIG. 2C . A bond wire  326  connects one of the signal common return pads to one signal common return terminal # 7   328 , and a bond wire  330  connects the other signal common return pad to another signal common return terminal # 9   332 . Again for symmetry, an equal number of bond wires  334  connect additional IC ground pads to the carrier ground plane  306  on each side of the signal common pad. 
         [0028]      FIG. 4  illustrates an IC die  402  disposed on an IC carrier  302  that is the same as shown in  FIG. 3 , including the ground plane  306  and twenty terminals # 1 - 20 . The IC die  402  differs from that of  FIG. 3  in that the first RF signal connection has a double pad  404  that accommodates two bond wires that couple it to terminal # 3   310 . Moreover, the first signal termination path has been split in a manner as shown in  FIG. 2B . The two first signal return pads  204  and  206  are coupled by bond wires  208  and  210  to first signal return terminals # 2   406  and # 4   314 . The RF signal common connections are unchanged from  FIG. 3 , and the second signal connections mirror the first signal connections. 
         [0029]    While the connection configuration described with respect to  FIG. 4  employs a termination circuit as shown in  FIG. 2B , the termination configurations of  FIGS. 2C and 2D  will serve better in some instances, providing more control over the mutual inductive coupling between a terminated RF signal (e.g., the first RF signal) and an isolation-target signal connection, such as the second RF signal connection or the RF common signal connection. 
         [0030]      FIG. 5  illustrates changes from the interconnections of  FIGS. 3 and 4  that affect both magnetic coupling and capacitive coupling between a terminated RF signal connection and a target signal connection. First, the IC die  502  is modified so that the first RF signal connection pad  504  is singular, reducing the physical area of the signal connection and hence its capacitive coupling to other signals. Second, the first signal termination path is changed to use separate termination impedance elements for each path, as shown in  FIGS. 2C and 2D , providing more control over magnetic coupling to other circuits. Third, the IC die  502  is disposed closer to the center of the IC carrier ground plane  306 . This serves to make the first signal current path, when the first signal is terminated, more perpendicular to the isolation-target current path of the RF common signal, at least when the RF common signal is terminated. While the overall increase in size of the RFC termination loop may, in fact, increase coupling to that signal line, there will be a modest reduction in the area of the first and second RF signal termination-current loops. Indeed, the configuration of  FIG. 5  may actually increase magnetic mutual coupling between the RF signal lines. As described below, minimum inductive coupling (or minimum capacitive coupling) between an RF signal line and an isolation-target signal line may not lead to the lowest net mutual coupling. In some instances, it may be useful to adjust one or the other of these quantities above the minimum that may readily be achieved. 
         [0031]    IC dies disposed in IC packages or on IC carriers are often provided with a protective covering, such as a glass-filled epoxy, or are otherwise brought into close proximity with a material that has a higher dielectric constant than air. Such dielectric may (and usually does) increase capacitive coupling between signal connections. Certain connection configurations can be employed to reduce the capacitive coupling. 
         [0032]    For example, as compared with  FIG. 4 , the bond wire  506  that connects the first RF signal to the first RF signal terminal # 3   310  has been reduced in area by making it a single wire. As another example, each of the first signal return pads  204  and  206  are connected to their corresponding first signal return terminals by two bond wires. A first of these is a bond wire such as  508 , which connects the first signal return pad  204  to the carrier ground plane  306  at a first connection point  510 . A second of these is a bond wire such as  512  that connects the corresponding first signal terminal  406  to the carrier ground plane  306  at a second connection point  514 . (Corresponding first and second bond wires  516  and  518  connect the other first signal return pad  206  to the corresponding first signal return terminal  314 .) The two bond wires may each be made as long as possible, consistent with remaining close to the signal line, so that they provide a ground potential adjacent to, or above, the signal line. By interposing a ground potential between a portion of the field between the signal lines, the capacitive coupling may be reduced. That is, the ground plane connection points  510  and  520  of the first bond wires  508  and  516  are made distal from the IC die  502 , significantly farther from the IC die  502  than are the connection points  514  and  522  of the second bond wires  512  and  518 , so that the return path bond wires can function, in part, as shields to reduce capacitive coupling to an isolation-target signal line. 
         [0033]    Further, the two bond wires may follow relatively closely to the first signal bond wire  506 , whereby the loop area of both of the current paths for the terminated first signal may be reduced, thus reducing mutual inductance coupling to the isolation-target signal (for the terminated case). Moreover, the terminated first signal loops may be given a distinct major axis orientation that may be made orthogonal to a major axis orientation of an isolation-target pickup loop, further reducing the magnetic coupling. Finally, the two terminated first signal conduction loops may be made as nearly as possible symmetrically opposite, thereby canceling net magnetic flux due to the termination currents, which yet further minimizes inductive coupling. 
         [0034]    After establishing minimum values for inductive and capacitive coupling that may readily be achieved by modifying the parameters noted above, it may be determined that further improvements may be made at particular frequencies of interest by tuning the capacitive and inductive coupling between signal connections. The net coupling can be nulled by tuning the mutual inductance (magnetic coupling) in combination with the mutual capacitance (capacitive coupling). The configuration details described above can be used to affect the values of both of these coupling types (magnetic and capacitive). Tradeoffs may then be made as necessary to obtain minimal mutual coupling over a very broad frequency range by minimizing the contribution of each type. Alternatively, mutual coupling may be reduced over a narrower frequency range by permitting a value of one or both mutual couplings to increase so as to obtain a coupling “null” at a frequency having a particularly stringent isolation requirement. 
         [0035]    A second RF signal is connected from an IC pad  526  to the second signal terminal # 13   318  via a bond wire  526 . The second RF signal is typically an isolation target with respect to the first RF signal, and may have the same stringent isolation requirements with respect to the first RF signal as the first RF signal has with respect to the second RF signal. Both RF signals may also have stringent isolation requirements with respect to the RF common signal connected to the terminal # 8   324 . Accordingly, it will typically be useful to provide termination paths and connections for the second RF signal that are substantially similar to those provided for the first RF signal. In the embodiment represented in  FIG. 5 , however, perpendicularity of the major termination loop axes is only maintained between the first or second RF signals and the RF common signal. Minimizing magnetic coupling between the two terminated signal current paths may therefore rely more heavily on increasing separation distance, on reducing the area of the termination current paths, and on causing mutual flux cancellation by establishing oppositely-directed current flow in the plurality of termination current paths. 
         [0036]    The termination current return paths for the RF common signal connected to terminal # 8   324  may each be configured as dual bond wires in a manner similarly as set forth above in regard to the first RF signal. Compared to the IC die shown in  FIG. 5 , it may be necessary to move the IC die toward the RF common terminal # 8   324  in order to minimize the net magnetic coupling of the terminated RF common signal to the terminated first RF signal and/or the terminated second RF signal. 
         [0037]    In order to meet the isolation requirements with respect to the most stringent isolation target, tests may be performed using different impedance element values. Such tests can be performed in order to ascertain an optimum balance of termination current between the two termination current return paths. 
         [0038]      FIG. 6  illustrates a generally similar connection scheme as described above with reference to  FIG. 5 . The IC die  602  and the carrier  600  of  FIG. 6  are both smaller than those shown in  FIG. 5 , reducing distances and increasing most mutual signal couplings. A first signal terminal # 2   650  is connected to a first signal IC pad  604  via a bond wire  606 . First signal termination is provided as part of the IC die  602  in a configuration as shown in one of  FIG. 2B ,  2 C or  2 D. Two first signal return pads  628  and  630  are employed to establish two oppositely-directed termination current paths that divide the termination current entering the IC via the bond wire  606 , such that the termination current returns via bond wires  608  and  616 . The bond wires  608  and  616  are connected by metal paths to two first signal termination current return terminals  654  and  656 . The metal paths may comprise single bond wires, but as shown in  FIG. 6 , each metal path comprises two bond wires ( 608  and  612 ,  616  and  658 ), as well as part of the ground plane  606 . 
         [0039]    The bond wires  608  and  616  are connected to the ground plane  606  at connection points  610  and  620 , respectively, which are relatively far from the IC die so that the ground potential may run somewhat closely to and, insofar as possible, between the first signal wire  606  and a primary isolation-target signal wire. The primary isolation wire will typically be that one of bond wires  626  (second RF signal connection) or  634  (RF common signal connection), to which the required isolation is most difficult to achieve. The bond wires  612  and  658  are connected to the ground plane  606  at points  614  and  622 , respectively. In both  FIG. 5  and  FIG. 6 , each of the four bond wires of the two first signal return paths are made long insofar as they can remain close to the corresponding first signal path, bond wire  606 . In  FIG. 6 , because the angle from the return path terminals  654  and  656  is more acute than in  FIG. 5 , the bond wires  612  and  658  cannot readily remain close to bond wire  606 . It may be useful to have them run relatively high from the ground plane, to provide more shielding and less capacitive coupling. Alternatively, it may be useful to shorten them such that connection points  614  and  622  approach connection points  610  and  620 , respectively, to reduce return path loop area, thereby reducing magnetic coupling. 
         [0040]    The second RF signal is connected from a terminal  618  to an IC pad  624 . The IC includes a termination circuit configuration similarly selected from among  FIGS. 2B ,  2 C and  2 D, or any other comparable termination circuit that splits the termination return current at least two ways. The second signal termination return current is provided paths similar or symmetrical to those provided for the first signal termination return currents. It is possible to configure the connections for the second RF signal, and the second RF signal return, differently than for the first RF signal, but more commonly they will be configured similarly. The RF common connections will also typically be similarly configured, including both forward and return connection paths, as are the connections for the first RF signal. Variations may be made, however, in order to tune net coupling between the various signal lines in particular embodiments. 
         [0041]    The RF common signal is connected from an RF common pad  632  to an RF common terminal  636  via a bond wire  634 . When the RF common pad  632  is not connected to either of the first or second RF signals, RF common termination current arriving via the bond wire  634  is split and returned via metal paths to RF common termination current return terminals  646  and  648 . As shown, the RF common return metal paths each include a plurality of path segments that are comparable to those of the first and second signal return paths. RF common return pads on the IC die  602  are connected via bond wires  638  and  642  to the carrier ground plane  606  at a point relatively distal from the IC die. Thereby, the bond wires  638  and  642 , which are at ground or other AC common voltage, may help shield the RF common connection wire  634  and thereby reduce capacitive coupling. Portions of the carrier ground plane  606  form the next segment of the paths, followed by the bond wires  640  and  644  that complete the RF common termination return paths to the carrier terminals  648  and  646 , respectively. 
         [0042]      FIG. 7  illustrates simulated net isolation between a first signal line and an isolation target signal line (e.g., a second signal line, or an RF common signal line). The graphs reflect net isolation for exemplary connection configurations generally as shown in  FIGS. 4  (lines “A”) and  5  (lines “B”). Mutual magnetic coupling is held constant at a value expected from the particular configuration. Mutual capacitive coupling between the nominally isolated signal lines varies logarithmically along the “X” axis. In actual embodiments, the capacitance can be affected not only by the connection configuration details as noted above, but also by dielectric material (such as packaging plastic or sealing epoxy) that may be disposed nearby or between the nominally isolated signal lines. The net isolation in dB varies along the “Y” axis, with lower negative numbers indicating higher isolation. As may be seen from a review of  FIG. 7 , the configuration that provides the best net isolation depends upon the level of capacitive coupling that is presumed. Such capacitive coupling level presumption is limited by the net capacitive coupling that can be achieved. 
         [0043]    The dotted lines (both A and B) illustrate isolation of the terminated first signal line to the RF common, while the solid lines illustrate isolation of the terminated first signal line to the second signal line when the second signal line is connected to the RF common line, and neither line is terminated. The solid lines indicate the more critical measurements. As may be seen, the coupling between the two signal lines has distinct complex interactions that result in “nulling” of the net mutual coupling. The nulling occurs at particular values of (simulated) capacitive coupling, because the frequency and mutual magnetic coupling are held constant. For values of total mutual capacitive coupling that are smaller than about 2 femtofarads, the solid line A indicates that a higher net isolation (lower net coupling) can be achieved with a configuration, such as that of  FIG. 4 , which is adjusted to provide lower mutual magnetic coupling. However, if the lowest capacitive coupling that can be achieved is approximately between about 2 and 5 femtofarads, the solid line B indicates that isolation of greater than −80 dB may be achievable by actually increasing the mutual magnetic coupling, in a circuit such as illustrated in  FIG. 5 . 
         [0044]    Any of the individual steps described hereinabove may be used to adjust either the mutual capacitive coupling between the first signal and the isolation-target signal. The best net isolation may not necessarily be obtained by having the lowest possible value for each type of coupling. When a critical isolation requirement is most difficult to meet over a fairly narrow frequency range, it may be better to use the described steps to adjust at least one of capacitive or inductive mutual coupling to a value that is larger than may be readily achievable, so that the interaction of the two types yields a net isolation that is greater than either the inductive or capacitive mutual coupling, alone, would provide. In many embodiments, this method will include splitting termination return currents for both of the signals in a manner as described above. 
       Conclusion 
       [0045]    The foregoing description illustrates exemplary implementations, and novel features, of a method of packaging and interconnecting integrated circuits to maintain high isolation between RF signal lines, and apparatus that can be configured to implement such method. The skilled person will understand that various omissions, substitutions, and changes in the form and details of the methods and apparatus illustrated may be made without departing from the scope of the invention. Numerous alternative implementations have been described, but it is impractical to list all embodiments explicitly. As such, each practical combination of the apparatus or method alternatives that are set forth above, and/or are shown in the attached figures, constitutes a distinct alternative embodiment of the subject apparatus or methods. Each practical combination of equivalents of such apparatus or method alternatives also constitutes a distinct alternative embodiment of the subject apparatus or methods. Therefore, the scope of the presented invention should be determined only by reference to the appended claims, as they may be amended during pendency of the application, and is not to be limited by features illustrated in the foregoing description except insofar as such limitation is recited, or intentionally implicated, in an appended claim. 
         [0046]    All variations coming within the meaning and range of equivalency of the various claim elements are embraced within the scope of the corresponding claim. Each claim set forth below is intended to encompass any system or method that differs only insubstantially from the literal language of such claim, if such system or method is not an embodiment of the prior art. To this end, each described element in each claim should be construed as broadly as possible, and moreover should be understood to encompass any equivalent to such element insofar as possible without also encompassing the prior art.