Abstract:
This disclosure provides active power filter methods and apparatus to control the PF, harmonics and/or ripple current associated with powering electrical devices. According to one exemplary aspect, an active power filter is configured to measure the momentary ac line output current, measure the momentary ac line input current and switch an energy buffer to provide additional current to the ac line output or draw current from the ac line input to control the PF associated with the device.

Description:
BACKGROUND 
       [0001]    This disclosure related to active power filters. According to one exemplary embodiment, this disclosure provides active power filter methods and apparatus for power factor (PF) and harmonic control of a power supply associated with a printing device. 
         [0002]    The primary purpose of a power filter is to control the PF associated with the powered device. The PF is the ratio of real power to apparent power, where the ideal PF is equal to 1. As a practical matter, the PF associated with a load (i.e. the power supply and the device powered by the power supply) is a metric which indicates the percentage of supplied power actually being used to operate the device. 
         [0003]    Another purpose of a power filter is to reduce the harmonic components associated with the input current and voltage. Typically, loads are not completely resistive because of the capacitive and inductive nature of the powered devices. Consequently, harmonics are generated which shift the input voltage and current out of phase. These harmonics can also contribute to reducing the efficiency of the powered device. 
         [0004]    To improve the PF and harmonic control of powered devices, it is common to use passive filters and active filters operatively connected to the power supply associated with the device. Commonly, passive filters are used because of their simplicity. Passive filters are primarily composed of passive elements, such as capacitors and inductors, which offset the advance or lag of the current phase to reduce the harmonics associated with the device. 
         [0005]    One disadvantage associated with passive filters is the need for relatively large components for dealing with large currents and voltages. 
         [0006]    There is a need for active power filters to accommodate large currents and voltages to reduce the component sizes necessary to control the PF and harmonics associated with a powered device, such as a printing device. 
       INCORPORATION BY REFERENCE 
       [0007]    U.S. Pat. No. 6,317,571 entitled “PRINTER FUSER HEATER CONTROLLER WITH POWER FACTOR CORRECTION,” issued Nov. 13, 2001 to Adams is totally incorporated herein by reference in its entirety. 
       BRIEF DESCRIPTION 
       [0008]    In one aspect of this embodiment, an active line filter is disclosed which comprises an ac line input; an ac neutral connection point; an ac line output; and an energy buffer, operatively connected to the neutral connection point and line output, wherein the active line filter is configured to measure the momentary line output current, measure the momentary line input current, switch the energy buffer to provide additional current to the line output when the momentary line output current is greater than the momentary line input current and switch the energy buffer to draw current from the line input when the momentary line output current is less than the momentary line input current. 
         [0009]    In another aspect of this embodiment, a printing apparatus is disclosed comprising a printing device; a power supply operatively connected to the printing device; and an active line filter comprising: an ac line input: an ac neutral connection point; an ac line output; and an energy buffer, operatively connected to the neutral connection point and line output, wherein the active line filter is configured to measure the momentary line output current, measure the momentary line input current, switch the energy buffer to provide additional current to the line output when the momentary line output current is greater than the momentary line input current and switch the energy buffer to draw current from the line input when the momentary line output current is less than the momentary line input current. 
         [0010]    In still another aspect of this embodiment, a method of operating an active line filter is disclosed which includes an ac line input, an ac neutral connection point or ac line output and an energy buffer operatively connected to the neutral connection point and line output, the method comprising A) measuring the momentary line output current; B) measuring the momentary line input current; C) switching the energy buffer to provide additional current to the line output when the momentary line output current is greater than the momentary line input current; and D) switching the energy buffer to draw current from the line input when the momentary line output current is less than the momentary line input current. 
     
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         [0011]      FIG. 1  is a schematic of an active power filter according to an exemplary embodiment of this disclosure. 
           [0012]      FIG. 2  is a graph of the distorted load current and corrected line current according to one exemplary aspect of this disclosure. 
           [0013]      FIG. 3  is another schematic of an active power filter according to an exemplary embodiment of this disclosure. 
           [0014]      FIG. 4  is a schematic of an exemplary control circuit associated with the control of an active power filter as illustrated in  FIGS. 1 and 3 . 
           [0015]      FIGS. 5 and 6  are schematics of the exemplary control circuit illustrated in  FIG. 4 . 
           [0016]      FIG. 7  is a schematic of another exemplary active power filter including a dual phase-locked switch mode for reducing ripple current. 
           [0017]      FIG. 8  is a schematic of an exemplary control circuit associated with the control of an active power filter as illustrated in  FIG. 7 . 
           [0018]      FIG. 9  is a graph of a typical distorted lie current, a corrected line current and the current associated with the two compensation circuits illustrated in  FIG. 7 . 
           [0019]      FIG. 10  is a magnified version of the graph illustrated in  FIG. 9 . 
           [0020]      FIG. 11  is a graph of the sum of the two compensation currents of  FIGS. 9 and 10 . 
       
    
    
     DETAILED DESCRIPTION 
       [0021]    The power usage in older legacy systems creates current harmonics in the power lines. In order to meet the new harmonics requirements, an active line filter in front of such system or integrated with the system can solve this problem. In this case no redesign of the system (e.g. Low Voltage Power Supplies and AC loads) is required. 
         [0022]    The here described power stage uses only one fullbridge mosfet switch and energy storage bulk capacitor for both the positive and negative mains cycle. Also, no blocking diodes are used, this function is taken over by the controlled use of the mosfet acting as flyback diode. In general this is a cost effective solution which uses relatively less power components. For this power circuit also a unique bipolar control circuit is provided. 
         [0023]    A power circuit for an active line filter should be able to take extra current from and supply extra current to the mains line. It should also be able to operate in the positive as well as the negative half mains cycle. The circuit illustrated in  FIG. 1  accomplishes these objectives. 
         [0024]    Referring to  FIG. 1 , when the momentary line out current is higher than the sinusoidal level the circuit shall supply extra current in order to support the mains line. In this mode the power circuit shall act as a normal buck converter. The energy is taken from the capacitor C. During the positive half mains period Q 3  is closed and Q 4  open. The V− line is now connected to the Neutral line. In buck mode Q 1  is acting as the power switch and Q 2  is acting as the flyback diode. During the negative half mains cycle Q 3  is open and Q 4  closed. The V+ line is now connected to Neutral. In this stage Q 2  acts as the power switch and Q 1  as the flyback diode (both current and voltage are negative in this mode). 
         [0025]    When the momentary line out current is lower than the sinusoidal value the circuit needs to draw extra current from the line. The circuit is now acting as a boost converter like in a normal pfc circuit. The capacitor voltage shall always be higher than the highest momentary mains voltage. 
         [0026]    During a positive half mains cycle and in boost mode, (Q 3  closed) Q 2  is acting as the boost switch and Q 1  as the flyback diode. 
         [0027]    In the negative period Q 4  is closed and now Q 1  is the boost switch with Q 2  acting as flyback diode. 
         [0028]    There are a couple of advantages with this topology:
       (mosfet) Switches can be turned on when they are in diode mode (synchronous rectifier) so that conduction losses are reduced.   The V− line can be used as return line for all control and driver circuits (Normal highside low side mosfet drivers can be used)       
 
         [0031]    Line  22  in  FIG. 2  shows a distorted load current. Line  24  is the corrected line current. When the load current is larger than the corrected line current energy is taken from the buffer capacitor. Its voltage shown by the line  20  is then going down. The average current of both lines is identical so that the average capacitor voltage is not changing. 
         [0032]      FIG. 3  shows a part of an active filter mainboard schematic according to an exemplary embodiment. Transformer T 5  is used to make a sine wave reference signal used in the control section which will be described with reference to  FIG. 4 . 
         [0033]    The primary side of this converter is connected directly across the energy buffer capacitors. 
         [0034]    The control circuit in  FIG. 4  controls the line current “I line” such that its shape is sinusoidal and it regulates the average buffer voltage “V+”. 
         [0035]    The overall feedback loop is the one which regulates the buffer voltage “V+”. This is done by the error amplifier which generates a dc signal which is fed into the DC controlled amplifier. If for example, the buffer voltage is too low, the dc signal will go up. This results in a larger sinewave signal on the output of the DC controlled amplifier. The “I compensation current” will now be changed such that the “I line” current follows the increased “Iref” signal. As soon as the average line current is larger than the average load current the buffer voltage will go up. There is a small sinewave signal of reversed polarity added to Iref so that it is also possible to feed some energy back into the mains line. Notably, it is useful to discharge the buffer capacitor in case it is charged too much. 
         [0036]    Continuing with the description of the control in  FIG. 4 , “I line” is subtracted from the “I ref” signal and the result “I error” is amplified in order to get sufficient gain in the feedback loop. This “High gain amplifier” is also used to add proper phase compensation. The output is used as the reference signal to control the compensation current. When the “I compensation” current is larger than “I compensation reference” plus hysteresis offset, Q 2  is turned on. “I compensation” is now ramping down. The di/dt rate is defined by the momentary line voltage and the inductance of L. As soon as this current comes below the “I compensation reference” min hysteresis offset, Q 2  is turned off and Q 3  turned on. The inductor current is now ramping up. The triangular compensation current is switching around the “I compensation reference” level. 
         [0037]    The advantages of this method are:
       Signals can be bipolar as the amplifiers have a plus and min supply line with the V− line as return path. Normal pfc controllers as well as pwm (pulse width modulated) and current mode regulators have only a single polarity.   The reaction speed is only limited by loop gain and di/dt capability.   The circuit is independent of the actual line polarity. The switchmode signal to Q 1  and Q 2  doesn&#39;t have to be reversed when line polarity changes.       
 
         [0041]      FIG. 5  shows a section of a Sorrento active line filter schematic which controls the energy buffer voltage. In  FIG. 6  the high gain amplifier and comparator section is shown. 
         [0042]    With reference to  FIG. 7 , illustrated is a basic schematic of a dual phase-locked power circuit for an active line filter. Notably, the power circuit previously described has only one switch mode circuit. Consequently, response speed is limited by the value of the used inductor. A low inductance value will give a fast response but will give also a significant ripple current. As the line impedance is very inductive and the load capacitive, a large ripple current will lead to significant ringing. The benefits associated with the addition of a second compensation circuit include the following:
       In situations where the load current changes very fast the power switches are controlled such that both inductors have a di/dt in the same direction. This will double the compensation speed.   When there is no fast change in load current both switching stages operable in opposite directions so that total ripple current is reduced.       
 
         [0045]    The control circuit in  FIG. 8  controls the line current “I line” such that its shape is sinusoidal and it regulates the average buffer voltage “V+.” It generates an “I compensation reference” which is used as input to the circuit described with reference to  FIG. 7 . The principle is to add a square wave signal to the first “I compensation” signal before it goes into the comparator and an inverted signal to the other “I compensation” signal. This results in an inverted switching of the two power stages when there is no large change in compensation current required. The graph of  FIG. 9  shows in the upper half, a typical distorted load current  130  and the corrected line current  132 . In the lower half the current of the two compensation sections is shown,  134  and  136 . 
         [0046]    The graph of  FIG. 10  shows again the distorted load current  130 , corrected line current  132  and the current in the two compensations circuits  134  and  136 . The sawtooth wave form of the two compensation lines are in opposite directions. But as soon as there is a fast change in load current, both currents move in the same direction. 
         [0047]    The lower line  140  in  FIG. 11  shows the sum of the two compensation lines. It is clearly visible that the ripple current compared to the compensation step is much lower. 
         [0048]    An “ideal” active line filter should immediately respond to fast load changes. This however is limited by the L value of the inductor. A smaller inductor value introduces a higher ripple current and hence, due to the nature of the line impedance, will lead to significant ringing. 
         [0049]    Then additional control circuit provided adds a squarewave to the compensation signals in such a way that it results in an inverted switching of one of the two power stages, when no large change in compensation current is required. This results in a lower ripple. However, as soon as there is a large compensation current required, the power switches are switched with an identical signal and move the currents in the same direction resulting in double speed switching. 
         [0050]    It will be appreciated that various of the above-disclosed and other features and functions, or alternatives thereof, may be desirably combined into many other different systems or applications. Also that various presently unforeseen or unanticipated alternatives, modifications, variations or improvements therein may be subsequently made by those skilled in the art which are also intended to be encompassed by the following claims.