Abstract:
A reference voltage source for an integrated circuit includes a first voltage reference that is adjustable, a second voltage reference, a differential sensing device to compare a voltage provided by the first voltage reference to a voltage provided by the second voltage reference, a controller to provide a trim control signal to the first voltage reference in response to an output of the differential sensing device for adjusting the first voltage reference and to provide a signal to power down the second voltage reference after the first voltage reference has been adjusted.

Description:
RELATED APPLICATION 
     This application claims priority to Italian Patent Application Serial No. RM2001A000521, filed Aug. 30, 2001, entitled “Ultra Low Power Tracked Low Voltage Reference Source.” 
     TECHNICAL FIELD 
     The present invention relates in general to a method and apparatus for generating a voltage reference, and, in particular, to a method and apparatus for generating a high precision, low-power voltage reference for a flash memory circuit. 
     BACKGROUND 
     In low-voltage low power flash memories, for example; where Vcc is between 1.65 and 1.95 V, there is a need for a highly precise voltage reference (Vref) source. This circuit is needed to calibrate the different on-chip power supplies required for operation of the memory. Usually Vref sources are bandgap reference voltage sources based on the compensated behavior of the P-N silicon diode junction. There are a number of bandgap reference voltage sources described in the literature. Many of these circuits offer good stability versus Vcc power supply, temperature range, and process parameter spread. 
     Unfortunately, precision bandgap reference voltage sources working at low Vcc voltages, such as Vcc of about 1.8 V, typically require a significant amount of current to operate. This current can be in the range of hundreds of microamps, which is too high for flash memories used in portable devices, such as cellular phones. The bandgap circuits also cannot be shut down in “power down” or in standby mode, otherwise latency would be too great when reading the memory in the power down or standby mode. While voltage reference circuits requiring only a few microamps are available, these circuits do not provide the stability required over a range of Vcc power supply voltages, temperatures and process parameter spreads. 
     For the reasons stated above and for additional reasons stated hereinafter, which will become apparent to those skilled in the art upon reading and understanding the present specification, there is a need in the art for a low current Vref source that has high stability over a range of Vcc power supply voltages, temperatures, and process parameter spreads. The above-mentioned shortcomings of traditional Vref sources and other problems are addressed by the present invention, at least in part, and will be understood by reading and studying the following specification. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is a block diagram of a memory circuit coupled to a processor and a voltage supply according to an embodiment of the invention. 
     FIG. 2 is a block diagram of a Vref source circuit according to an embodiment of the invention. 
     FIG. 3 is a block diagram showing additional details of components of the Vref source circuit according to an embodiment of the invention. 
     FIG. 4 is a timing diagram showing operation of a Vref source circuit according to an embodiment of the invention where Vref is greater than Vbg. 
     FIG. 5 is another timing diagram showing operation of a Vref source circuit according to an embodiment of the invention where Vref is less than Vbg. 
    
    
     Although, various embodiments have been illustrated using particular electronic components it will be understood by those of ordinary skill in the art that other circuit elements could be used to implement the invention and that the present invention is not limited to the arrangement of circuit elements disclosed. Moreover, it will also be understood in the art that the present invention could be applied to a Vref source circuit for use in devices other than flash memory circuits that operate on very low supply voltages. Therefore, the present invention is not limited to a Vref source circuit for very low voltage flash memory. 
     DETAILED DESCRIPTION 
     FIG. 1 shows a computer system  100  including a memory  110 , a power supply  130  and a processor  140 . Memory  110  includes a memory array  112  of nonvolatile memory cells (which can be flash memory cells), an on-chip reference voltage source  200  for providing stable reference voltages for operation of the memory and a controller  120  that controls detailed operations of memory  110  such as the various individual steps necessary for carrying out writing, reading, and erasing operations. Memory  110  also includes an address decoder circuit  122  for decoding and selecting addresses provided by processor  140  to access appropriate memory cells in memory array  112 , and an I/O circuit  124  for providing bi-directional communications between processor  140  and memory circuit  110 . 
     FIG. 2 shows a simplified block diagram of a Vref source circuit  200  according to one example of the invention. The circuit includes low voltage bandgap reference  210 , low current trimmable Vref source  212 , differential sensing device  214 , track control  216 , clock generator  218  and astable circuit  220 . Low voltage bandgap reference  210  is preferably a high precision bandgap reference voltage source that is set to a predetermined voltage. In operation, it may draw relatively high current, for example, in the range of 200 μA. Low current trimmable (adjustable) Vref source  212  is a relatively low current consumption Vref source that has relatively low precision over changes in Vcc, temperature, and process parameters. Differential sensing device  214  compares two input voltages and outputs a result that indicates which voltage is higher. Differential sensing device  214  may be a comparator or a differential amplifier or other differential voltage sensing device. Its inputs are the voltage reference outputs of low voltage bandgap reference  210  and of trimmable Vref source  212 . Track control  216  includes logic circuitry for supervising the operation of Vref source circuit  200  and is clocked by a high frequency clock signal provided by clock generator  218 . 
     FIG. 3 shows trimmable Vref source  212  in more detail. In this example, trimmable Vref source  212  includes current source  302 , RC filter  310  and decoder  308 . Current Source  302  is powered by Vcc and feeds resistor ladder  304 . Individual resistors of resistor ladder  304  are selected by switches  306 . Switches  306  are activated by the output of decoder  308 . In the example shown in FIG. 3, decoder  308  is a 7-bit decoder. Resistor ladder  304  thus includes a series of 128 resistors selectively tapped so that the resistors can be shunted to ground by any one of the switches  306 . FIG. 3 shows 128 transistor switches, T 1 -T 128 , only one of which at any one time are selected by decoder  308  according to the value of the 7 bits of vtrim. Tolerance of the resistors of resistor ladder  304  corresponds to a Vref trimming resolution of 5 mV, more than adequate for all practical purposes in a flash memory. Other tolerances can, of course, be selected depending on the needs of a particular circuit design. RC filter  310  may be included to filter any relatively high frequency Vcc noise from reaching current source  302 . 
     Vref source circuit  200  operates, in general, as follows., At power-up, a reset signal resets Track Control  216  to an initial state. The logic signal track_enable input to Track Control  216  is, however, initially at “0” preventing operation of Track Control  216  immediately following the reset. The output Vbg of the Low voltage Bandgap is also disabled by the bg_enable signal provided by track controller  216 , which is at “0” following reset. Trimmable Vref source  212  activates, providing its output Vref to one input of differential sensing device  214 . Differential sensing device  214  is also initially disabled by the comp_enable signal provided by track controller  216 , which is at “0”. 
     The track_enable signal input to track controller  216  is a periodic, relatively low frequency short pulse, of 1 KHz, for example, generated by low current astable circuit  220 . Astable circuit  220  can be implemented as a current controlled oscillator, known to those of ordinary skill in the art. For example, a 4 μs period low current oscillator followed by a frequency divider (f/256), can be employed in order to reduce capacitance area. In the example, astable circuit  220  provides a 4 μs pulse every 1 ms. This duty cycle provides good tracking with minimal power consumption. The maximum time in which the tracking circuit is active, Tactive, in the worst case, can be calculated as follows: 
     
       
           T active =[ T clock*(2{circumflex over ( )} N+k )]  Formula 1 
       
     
     where Tclock is the clock period; N is number of bits of the vtrim signal and k is the number of latency clock cycles, which will depend on the particular implementation. In the present example, k is 3, Tclock is 100 ns and N is 7. If the current consumption of low voltage bandgap reference  210  plus the current consumption of differential sensing device  214  plus the current consumption of track control  216  is Ipeak, then the average current consumption can be determined by: 
     
       
           Iav=I peak* T active/ Ttrk   —   enbl+Ilcr   Formula 2 
       
     
     where Ilcr is the current of low current trimmable Vref source  212 , Ilcr is 5 μa, Iav is 10 μA, Ipeak is 200 μA, and Tactive is 128 μs. Thus, in this example, Ttrk_enbl is 5.12 ms. This example is based, of course, on the worst case. If, during normal tracking, Tactive is 5 times Tclock, then track_enable will be 20 μs. For this reason, a 1 kHz cycle for astable circuit  220  is sufficient. 
     The track_enable pulse also enables track control  216  to turn on clock generator  218  which runs at a much higher frequency than astable circuit  220 , in the range of about 10 MHz, for example. After track_enable has transitioned to logic “1” clock generator  218  begins to run. The first clock pulse is received by track controller  216 . Vref_start also by now has reached logic “1.” Track control  216  switches bg_enable to “1”, enabling power to low voltage bandgap reference  210 . Track control  216  also switches Comp_enable to “1” thus enabling differential sensing device  214 . 
     Low voltage bandgap reference  210  takes some time to stabilize its output voltage, Vbg, after power-up. Track control  216  will not actually start the tracking operation until bg_start goes to “1”, signaling that low voltage bandgap reference  210  has a stable output. Once bg_start is “1”, and, as soon as the next next clock pulse is received, track control  216  starts to analyze the comp_out signal of differential sensing device  214 . If Vref is lower than Vbg, comp_out is “0” and the digital 7 bit output vtrim is incremented by 1. The vtrim signals trims or adjusts trimmable Vref source  212  to a higher Vref value. At the next clock cycle, comp_out is again evaluated by track control  216 , and, if Vref is still too low, vtrim is again incremented by 1. This operation repeats until Vref is higher than Vbg. When comp_out transitions from “0” to “1” signaling that the tracking operation has been completed, comp_enable, clock_enable, and bg_enable go to “0” shutting off the differential sensing device  214 , low voltage bandgap reference  210  and clock generator  218 . Trimmable Vref source  212  is now trimmed essentially to the same value as the low voltage bandgap reference  210  and provides Vref to the whole flash memory, as needed. 
     After about 1 ms, at the first clock pulse after the track_enable rising edge, track control  216  resumes its operation. First, bg_enable and comp_enable to go “1” powering low voltage bandgap reference  210  and differential sensing device  214 . As soon as the output Vbg is stable, bg_start goes to “1,” again enabling operation of track control  216 . Comp_out is then evaluated by track control  216 . If adjustment of Vref is needed, vtrim signals are increased or decreased by 1 every clock pulse, thus fine-tuning trimmable Vref source  212 . As the trimming is completed, (i.e., the device is calibrated) differential sensing device  214 , low voltage bandgap reference  210  and clock generator  218  are again powered down. 
     The operation of the present invention is illustrated in the timing diagrams of FIGS. 4 and 5. FIG. 4 shows an example where Vref is greater than Vbg. FIG. 5 shows an example where Vref is less than Vbg. At t 1 , Vref_start is already active. Track_enable transitions from “0” to “1,” and Comp_enable, clock_enable, and bg_enable activate comparator  214  and low voltage bandgap source  210 , respectively. Vbg ramps in response to bg_enable and then stabilizes. At t 2 , bg_start goes to “1” signaling that Vbg is now stable. As soon as the next clock pulse comes in, track control  216  starts to analyze the comp_out signal. Adjustment will take place (trimming Vref down is shown in FIG.  4  and trimming verf up is illustrated in FIG. 5) until comp_out transitions at t 3 . After trimming has been completed, comp_enable, clock_enable, bg_enable and bg_start transition to zero to conserve power. 
     Considerable power savings can be achieved with the present invention. Allowing for example 600 ns from the shut off state to stabilize Vbg, and an average of 2 clock cycles (200 ns, for example) for trimming, the trimming operation may require 1 μs. Since the period of the track_enable pulses is 1 ms, low voltage bandgap reference  210  and differential sensing device  214  are active and require power only for 1 μs every ms (duty cycle 1/1000). If their total operating current is 200 μA, for example, then the actual average current is 200/1000=0.2 μA. Considering that trimmable Vref source  212  typically draws 10 μA, the increment of 0.2 μA, (2% of the trimmable Vref source  212 ) is practically negligible. Current consumption may no doubt be even less in many instances. 
     Since low voltage bandgap reference  210  is stable over changes in temperature and Vcc voltage, as well as process spread, its stability is effectively transferred to the trimmable Vref source  212 , with an additional power consumption penalty of only 0.2 μA. Of course, during the gap of 1 ms between track_enlable pulses there is no tracking control. This is not likely to present problems. Since process variations occur only at the time of fabrication of the memory they should not be a factor. Likewise, temperature variations are also negligible because they occur relatively slowly compared to the speed at which the invention operates. Slow Vcc variations can also be tracked without a problem. Thus, the only variations potentially affecting the stability of trimmable Vref source  212  would be any noise on Vcc occurring during the 1 ms time frame where there is no tracking control. If such noise is a problem, the trimmable Vref source  212  can easily be designed to be stable with fast Vcc variation occurring in the 1 ms time frame without consuming additional power, by means of a simple RC filter on its power supply Vcc. In conclusion, exceptional Vref stability is accomplished by embodiments of the invention with inexpensive additional circuitry and practically negligible current consumption.