Abstract:
An apparatus for electromagnetic processing comprises a modulator for generating one or more elements representative of an input signal; a divider controlled by the one or more elements and receiving an electromagnetic wave to generate a modified signal; a comparator for comparing the modified signal to a reference signal and for generating a processed signal based upon the comparison; and a channel number calculator for selecting a channel for the processed signal, wherein the input signal incorporated the channel selection.

Description:
FIELD OF THE INVENTION 
     The present invention relates generally to electromagnetic processing, and more particularly, the present invention relates to wideband signal processing. 
     BACKGROUND OF THE INVENTION 
     Electromagnetic waves and signals (hereinafter “waves”) are utilized for many different purposes. For example, electromagnetic waves may be processed in order to convey intelligence, such as by attenuating and/or amplifying electromagnetic wave characteristics, for instance, as is seen when modulating amplitude, frequency or phase of an electrical current or radio frequency (RF) wave to transmit data. As another example, power may be conveyed along a wave in a controlled fashion by attenuating and/or amplifying electromagnetic wave characteristics, such as is seen when modulating voltage or current in a circuit. Moreover, the uses may be combined, such as when intelligence may be conveyed through a wave by processing power characteristics. 
     Electromagnetic wave characteristic processing may be accomplished through digital or analog techniques. Digital and analog attenuation and/or amplification may also be combined, that is, the same wave may be subject to various types of digital and/or analog attenuation and/or amplification within a system in order to accomplish desired tasks. 
     However, processing electromagnetic wave characteristics may be difficult. For example, choosing an appropriate technique or component to modify a wave characteristic may be difficult for a number of reasons. One of those reasons involves the type of wave to be modified. For example, low frequency waves, such as 60 Hz power waves, may need different processing techniques than high frequency waves such as 24 GHz radar waves. It is common practice therefore to use different components, with different characteristics, for different waves. For example, a switching semiconductor used within a computer for 60 Hz power waves has different power handling characteristics from a power semiconductor used in a 24 GHz radar system. 
     One attempt at standardizing techniques and components that has recently been used is to use characteristics of the wave as information to modify the wave. For example, by translating a wave into polar coordinates with amplitude and phase characteristics, either or both characteristics may be used and/or manipulated in such a manner so as to provide standardized techniques for various wave frequencies. However such attempts to date have been constrained by application difficulties. For example, attempts that use multiple amplifiers have suffered from difficulties attendant to amplifier combining. Specifically, components, such as transformers or quarter wave lines, are used to sum the output of the amplifiers in order to drive the load. These components add to the cost and size of the amplifier array. 
     Accordingly, it would be helpful to the art of electromagnetic processing to provide efficient, and at the same time, accurate techniques for the processing of electromagnetic waves. 
     SUMMARY OF THE INVENTION 
     Embodiments of the present invention include apparatus, methods and articles of manufacture for processing electromagnetic waves and signals. In one embodiment, an apparatus for electromagnetic processing is provided comprising a modulator for generating one or more elements representative of an input signal; a divider controlled by the one or more elements and receiving an electromagnetic wave to generate a modified signal; a comparator for comparing the modified signal to a reference signal and for generating a processed signal based upon the comparison; and a channel number calculator for selecting a channel for the processed signal, wherein the input signal incorporates the channel selection. 
     In another embodiment, a method of wideband processing a phase component signal is provided comprising generating one or more elements representative of an input signal; diving an electromagnetic wave based on the one or more elements to generate a modified signal; comparing the modified signal to a reference signal; and generating a processed signal based upon the comparison. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         FIG. 1  is a block diagram illustrating an exemplary transmitter. 
         FIG. 2  is a block diagram illustrating an embodiment of a wideband modulator for use in the transmitter of  FIG. 1 . 
         FIG. 3  is a schematic diagram illustrating an embodiment of a sigma-delta modulator used in a wideband modulator of  FIG. 2 . 
         FIG. 4  is a schematic diagram illustrating another embodiment of a sigma-delta modulator used in a wideband modulator of  FIG. 2   
     
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     Embodiments of the present invention include apparatus, methods and articles of manufacture for processing electromagnetic waves and signals. For illustration purposes, an exemplary embodiment comprises a wideband modulator adapted for processing electromagnetic waves and signals. The wideband modulator as disclosed herein may be implemented in a wide range of applications, such as, for example, a transmitter, receiver, transducer, etc. For purposes of illustration, an exemplary transmitter is disclosed in  FIG. 1  in which is incorporated a wideband modulator in accordance with an embodiment of the present invention. 
     The exemplary transmitter  10  illustrated in  FIG. 1  may include, for example, a baseband processor  100  adapted for receiving an input signal, an amplitude/phase signal processor  101 , wideband modulator  102 , adaptive phase realignment component  103 , power amplifier  104  and one or more load lines  105  connected to an antenna. The details of transmitter  10  and its various components are described in more detail below. 
     The term “signal” as is used herein should be broadly construed to include any manner of conveying data from one place to another, such as, for example, an electric current or electromagnetic field, including without limitation, a direct current that is switched on and off or an alternating-current or electromagnetic carrier that contains one or more data streams. Data, for example, may be superimposed on a carrier current or wave by means of modulation, which may be accomplished in analog or digital form. The term “data” as used herein should also be broadly construed to comprise any type of intelligence or other information, such as, for example and without limitation, audio, such as voice, text and/or video, etc. 
     As illustrated in  FIG. 1 , the baseband processor  100  may be a digital signal processor in this embodiment, such as a digital signal processor capable of generating a power control signal and a data control signal in response to the input signal, which may be, for example, a baseband signal. As described in more detail below, the electrical power may be regulated by the data control signal in order to generate an output signal for transmission that is an amplified version of the input signal. 
     The data control signal generated by baseband processor  100  in this embodiment comprises an electromagnetic wave that contains data derived from the input signal. The data control signal is passed from baseband processor  100  to amplitude/phase signal processor  101 . In one embodiment, I,Q data is converted by baseband processor  100  into a polar signal to create an analog or digital data control signal that contains the amplitude wave characteristic of the input signal, a m , and an electromagnetic signal that contains the phase wave characteristic of the input signal, a p . For example, a rectangular to polar converter may be used to output polar coordinates in the form R, P(sin) and P(cos). The R coordinate represents the amplitude characteristic of the wave. The P(sin) and P(cos) coordinates represent the phase characteristic of the wave. 
     The amplitude and phase characteristics of the input signal may then be transmitted through separate paths to power amplifier  104 . The amplitude characteristics of the original input signal may be modulated as a series of digital pulses comprising a digital word quantized into bits B 0  to B n-1 , with a Most Significant Bit (“MSB”) to Least Significant Bit (“LSB”). The digital word may be of varying lengths in various embodiments. 
     The phase characteristic, in turn, may be processed separately and then applied to power amplifier  104 . One exemplary manner for processing of the phase characteristic is illustrated in  FIG. 2 .  FIG. 2  shows, in detail, exemplary embodiments for the signal processor  101 , wideband modulator  102  and adaptive phase realignment  103  of  FIG. 1 . 
     In the present embodiment, the phase data from the input signal is first preferably passed through a data scaling processor  120 , which scales amplitude of the data signal appropriately. The change in signal amplitude produced by data scaling processor  120  is calculated to compensate for any gain in the output signal from the wideband modulator  102 . The scaling of the signal may be accomplished through any conventional means compatible with the data format, such as, for example, in a preferred embodiment the phase data signal is digital and scaling may be accomplished by digital processing. In this embodiment, wideband modulator  102  is inherently a frequency modulator, so that translation of data for frequency and phase representations of the data occurs via dθ/dt  123  shown in  FIG. 2 . 
     The phase component signal is then preferably passed through modulation compensation (equalization) filter  121 , which is calculated to have a magnitude and phase response that is the inverse of the closed loop response of wideband modulator  102 . As will be discussed below, in some instances, modulator  102  has an inherent design bandwidth to minimize noise in the signal. Limiting of the bandwidth in this manner, however, may cause a roll-off, that is, diminution, of the higher frequency components of the signal. Equalization filter  121  and overall modulation response filter  122  compensates for roll-off by increasing the gain of these higher frequency components, thus producing a more even (flattened) frequency response for the system and effectively extending the modulation bandwidth of wideband modulator  102 . The equalization filter  121  is preferably implemented digitally, using a digital signal processor, although not limited thereto, and may be either a FIR (finite impulse response) or IIR (infinite frequency response) filter, as examples. The phase component data may also be passed through overall modulation response filter  122 , which is calculated to set the overall passband response of wideband modulator  102  (e.g., 4 MHz). Overall modulation response filter  122 , similar to equalization filter  121 , may be an analog or digital FIR or IIR filter. Functionally, filters  121  and  122  may be combined into a signal filter where desired. 
     In the present embodiment, the baseband input signal may be modulated onto a carrier wave of a selected center frequency in wideband modulator  102 . The center frequency about which a given signal is to be modulated is determined by a channel calculation, by which the carrier wave frequency (e.g., 1880 MHz) is divided by the frequency of the reference source to establish a channel for the signal. 
     In the present embodiment, the channel calculation yields a number that has an integer part and a fractional part. As shown in  FIG. 2 , channel calculator  124  received the channel number from baseband processor  100  and determines a selectable non-whole number by which the carrier wave of wideband modulator  102  is to be divided, allowing the selection of a channel in which the phase data signal is to be modulated. As an illustration of the channel calculation procedure, assuming a carrier wave frequency of 1880 MHz as an example, this number may be 23.5 to 24.5 as determined from the reference frequency. The fractional portion of this number is then combined with the data signal, which is passed to sigma delta modulator (SDM)  125  in wideband modulator  102 . SDM  125  is used in connection with phase-locked loop (PLL)  126  to achieve wideband modulation of the input signal onto a carrier wave. SDM  125  serves to randomize and oversample the inputted phase data, with the average of multiple samples of the output being equal to the input. The SDM  125  in this embodiment operates in a manner so that inherent quantization noise from the digitizing process may be frequency shaped, so that at the desired frequencies, the noise is low. 
     SDM  125  may comprise, for example, a series of adders/accumulators and feedback components for inputting the fractional phase/channel number data (which may be an analog or digital signal) and outputting a digitized series of integers that equal the fractional input. The SDM  125  is preferably configured in the present embodiment in such a manner that the input range is sufficient for phase modulation data as well as the fractional portion of the channel number. In one exemplary embodiment, SDM  125  is a three bit system, which is thus capable of producing eight different output numbers (e.g., −3, −2, −1, 0, 1, 2, 3, and 4), although as should be understood, in other embodiments SDM  125  may comprise any desired number of bits or elements. In the present embodiment, SDM  125  preferably produces four output integers for each sample of the input, yielding an oversampling rate of four times the input. Sampling of the input modulating data in SDM  125  in this manner may introduce noise on the input modulating signal. Any such noise may be filtered by low-pass loop filter  131  in PLL  126 .  FIGS. 3 and 4  illustrate two exemplary circuit topologies for the SDM  125 .  FIG. 3  illustrates a MASH III topology and  FIG. 4  illustrates a 3 rd  Order Loop topology. As should be understood, however, other suitable circuit topologies may also be utilized for the SDM  125  where desired. 
     The output of SDM  125  in the present embodiment is then combined with the integer portion of the channel number received from channel calculator  124 . In the example discussed herein, the combination would produce a number from 20 to 28. The combination of the fractional and integer portions of the channel number is input to divider  128  in the present embodiment and used to lock PLL  126  to the desired RF carrier. 
     The PLL  126  in the present embodiment is preferably used to modulate a wave signal synthesized by an RF carrier wave signal source, such as carrier wave source  129 , using the phase portion of the input signal. Carrier wave source  129  may be any source of electromagnetic waves that is capable for producing a carrier wave, such as a radio frequency voltage-controlled oscillator (VCO). 
     As shown in  FIG. 2 , in the present embodiment, the frequency of reference source  127  (or a division thereof by some number) is compared with the output frequency of carrier wave source  129 , divided by the series of numbers received by divider  128  from SDM  125  and channel calculator  124 . Reference source  127  may comprise a VCO of a constant or substantially constant frequency or may be derived from a source at another frequency. 
     As shown in  FIG. 2 , phase-frequency detector (PFD)  130  is used to compare the relative phases of the two signals and then outputs a signal that is proportional to the difference (phase shift) between them. This output signal is utilized to adjust the frequency of carrier wave source  129 , so that the phase difference measured at PFD  130  is substantially close and preferably equal to zero. Hence, the phase of the signal is locked by the feedback loop to prevent unwanted drift of the signal phase, due to variations (i.e., distortion) in the phase and frequency of carrier wave source  129 . 
     As illustrated in  FIG. 2 , the feedback signal from carrier wave source  129  is passed through divider  128 , with the division ratio of the divider controlled by the series of numbers representing the phase component information received from SDM  125  and the channel information received from channel calculator  124 . The resulting signal is passed to PFD  130 , where it is compared with the signal from reference source  127 , as noted above. This combined signal is passed through low-pass loop filter  131 , and combined with the carrier wave signal of carrier wave source  129 . 
     In the present embodiment, SDM  125  is being utilized to perform wideband modulation of the phase data input to SDM  125 . Since the phase data input to SDM  125  is not constant, synchronizing SDM  125  to the output of divider  128  may introduce a frequency offset that is dependent on the modulation signal. Accordingly, it may be desired in certain embodiments that SDM  125  and divider  128  be synchronized by reference source  127 . For example, buffering may be used between the output of SDM  125  and the input of divider  128 , so that divider  128  may complete the divide count before updating with a new series of sample numbers. 
     As shown in  FIG. 1 , adaptive phase realignment component  103  may also be used to dynamically adjust the PLL response, to ensure that the equalization filter  121  and the closed loop response of the PLL  126  are closely matched. Adaptive phase realignment component  103  preferably measures the output phase of wideband modulator  102  and compares it to a theoretically perfect version that is derived from the baseband input data and the center frequency information received from channel calculator  124 . The result of this comparison is used to adjust the loop gain of PLL  126  in wideband modulator  102 . This feedback system operates to minimize the error in the transmitted signal. Adaptive phase realignment component  103  preferably operates while the transmitter is in service and reduces the need for manual calibration of the system. 
     An exemplary embodiment of adaptive phase realignment component  103  is illustrated in detail in  FIG. 2 . As should be understood, other suitable embodiments for the adaptive phase realignment  103  may also be utilized where desired. The adaptive phase realignment component  103  as illustrated in  FIG. 2  may include, for example, a digital phase lock loop (DPLL)  140 , a reference error filter  142 , a carrier phase detector/track &amp; hold  144 , a gain-error detector  146  and a RF phase quantizer  148 . 
     DPLL  140  operates to align the ideal phase to real RF phase by removing any constant phase offset, Φ, and random drift, ω drift , due to the delays through SDM and RF quantized demodulation process.
 
 RF   —   VCO _Out=cos(ω c   t+K   tot (1+δ) d   n    ∫g ( t ) dt+ω   drift   t+Φ )
 
     Reference error filter  142  operates to produce a reference phase-error waveform from estimated loop filter transfer function. This reference error signal serves as a basis function for the measured true phase error. By multiplying the true phase error signal with the reference error signal, the polarity of the PLL gain error preferably matches the polarity of the automatic calibration feedback output. In addition, the average of the automatic calibration feedback output is preferably proportional to the amplitude of the PLL gain error (regardless of the polarity of the phase information signal). 
     Carrier phase detector/track &amp; hold  144  operates to provide for direct comparison of digitally summed carrier and phase (ideal) to sampled VCO RF true phase output. The carrier phase detector/track &amp; hold  144  removes phase ambiguity, such as a 2p-radian phase ambiguity as an example, and provides phase/frequency detection. 
     Gain-error detector  146  operates to produce the estimated deltas of the PLL gain error and provides a correction signal to the PLL frequency phase detector to adjust the loop gain. 
     RF phase quantizer  148  is used to sample the RF carrier to extract the baseband phase information to retrieve the modulating signal. This function is realized using an A/D converter as an example. 
     Returning now to  FIG. 1 , the processed wave output from wideband modulator  102  preferably has a constant envelope, i.e., it has no amplitude variations, yet it has phase characteristics of the original input wave. This output wave may then be sent where desired, such as to power amplifier  104 , which may comprise any of a variety of suitable types of amplifier components. In one exemplary embodiment, power amplifier  104  is adapted to act as a current source when it is appropriately regulated by the digital word output from the amplitude component. The amplitude portion of the input signal is separately passed from amplitude/phase signal processor  101  to power amplifier  104  and may be used to actuate individual segments within power amplifier  104 , to amplify or attenuate the phase modulated carrier signal in relation to the original input signal. This produces an output current from power amplifier  104  that represents an amplified or attenuated carrier wave containing the intelligence from the input signal. 
     In some embodiments, for example, with certain transmitter, receiver, and transceiver embodiments, the devices may be specialized for particular input signals, carrier waves and output signals, e.g. various types of cell phones, such as CDMA, CDMA2000, W-CDMA, GSM, TDMA, as well as various other types of devices, both wired and wireless, e.g. Bluetooth, 802.11a, -b, -g, radar, 1×RTT, radios, GPRS, computers and computer or non-computer communication devices, handheld devices, etc. Among the modulation schemes supported by the various embodiments include, for example, GMSK, which is used in GSM; GFSK, which is used in DECT &amp; Bluetooth; 8-PSK, which is used in EDGE; OQPSK &amp; HPSK, which are used in IS-2000; p/4 DQPSK, which is used in TDMA; and OFDM, which is used in 802.11. 
     Embodiments may utilize both analog and digital components, where desired, insofar as these embodiments manipulate waves and signals requiring both. For example, cell phone embodiments may utilize both analog and digital components. Various types of system architectures may also be utilized for constructing the embodiments. For example, embodiments or various components may be provided on a semiconductor device where desired, such as an integrated circuit or an application-specific integrated circuit composition; some examples include silicon (Si), silicon germanium (SiGe) or gallium arsenide (GaAs) substrates. 
     Having thus described a few particular embodiments of the invention, various alterations, modifications, and improvements will readily occur to those skilled in the art. Such alterations, modifications and improvements as are made obvious by this disclosure are intended to be part of this description though not expressly stated herein, and are intended to be within the spirit and scope of the invention. One of ordinary skill in the art will accordingly appreciate that embodiments of the invention or various components and/or features thereof may be entirely comprised of hardware, software and/or may be a combination of software and hardware. Accordingly each of the blocks of the drawings, and combinations of blocks of the drawings, may be embodied in many different ways, as is well known to those of skill in the art. Accordingly, the foregoing description is by way of example only, and not limiting. The invention is limited only as defined in the following claims and equivalents thereto.