Abstract:
An apparatus for converting a multidigit decimal number into a binary number. In a preferred embodiment, the apparatus includes a register for holding the multidigit decimal number; first conversion logic, coupled to the register, for simultaneously converting a first pair of decimal digits in the multidigit decimal number, into a first binary representation and second conversion logic, coupled to said first conversion logic and the register, for simultaneously converting a second pair of decimal digits in the multidigit decimal number and the first binary representation into a second binary representation of a decimal number defined by the first and second pair of decimal digits.

Description:
This is a divisional of copending application Ser. No. 07/532,729 filed on 6/4/90, now U.S. Pat. No. 5,031,138, issued Jul. 9, 1991. 
    
    
     BACKGROUND OF THE INVENTION 
     1. Field of the Invention 
     This invention relates to circuits for converting a plurality of decimal digits to a binary representation. 
     2. Related Art 
     Binary division, as performed by digital computers, has been conventionally accomplished by iteratively subtracting multiples of the divisor from a partial dividend. By performing division in such a manner, multiple bits of the quotient can be developed in each iteration, thus saving a significant number of machine cycles over the course of a divide operation. 
     In a typical divide iteration, the following operation is performed: 
     
         Rn=PDn-Mn*D 
    
     where, 
     R n  =remainder at the end of iteration n 
     PD n  =partial dividend at the start of iteration n 
     D=divisor (1/2≦D≦1) 
     M n  =divide multiple used in iteration n 
     (An &#34;*&#34; indicates multiplication) 
     For a 2-bit divide, PD n+1  =4*R n  (left shift of two bits). If M n  is restricted to the values -2, -1, 0, +1, +2 then, 
     
         |R.sub.n /D|≦2/3, or |PD.sub.n /D-M.sub.n|≦2/3 
    
     Therefore, once the ratio of PD n  /D is known, the divide multiple M n  can be determined by Table I: 
     
                       TABLE I______________________________________Xn = PDn/D        Mn______________________________________4/3 ≦ X.sub.n ≦ 8/3             21/3 ≦ X.sub.n ≦ 5/3             1-2/3 ≦ X.sub.n ≦ 2/3             0-5/3 ≦ X.sub.n ≦ -1/3             -1-8/3 ≦ X.sub.n ≦ -4/3             -2______________________________________ 
    
     Further, Q n  can be determined by the relationships of TABLE II: 
     
                       TABLE II______________________________________Mn          Qn(Rn &gt; or = 0)                    Qn(Rn &lt; 0)______________________________________2           2            11           1            00           0            3-1          3            2-2          2            1______________________________________ 
    
     As indicated above, a typical divide operation will include two serial operations: 1) determine M n  from PD n  /D; 2) determine R n  by R n  =PD n  -M n  *D. In prior techniques it has been shown that Mn+1 can be generated in parallel with Rn. Hence, the iteration time is limited by generating Rn. Conventionally, M n  is determined by providing both PD n  and D to decoders (one for negative PDn values and a separate decoder for positive PD n  values) and determining M n  by using look up tables. 
     To determine M n , only the high-order bits of PD n  and D are needed. Since PD n  =4R n-1  =4(PD n  -1 -M n-1  *D), the higher order bits of PD n  (designated PD n  &#39;) can be generated in parallel with PD n  from the higher order bits of PD n-1  and M n-1  *D. The PD n  &#39; so generated ignores the carry-in from the lower order bits. This error can be compensated for by selecting the multiple boundary in the overlapped region between the multiples. Since: 
     
         PD.sub.n-1 =4R.sub.n-2 =4(PD.sub.n-2 -M.sub.n-2 *D) 
    
     then ##EQU1## Therefore the high-order bits of PD n  (PD n ) and hence Mn, can be determined from PD n-2 , M n-2 , and M n-1 . 
     The quotient bits Q n  (2 bits per iteration) are determined by the relations: 
     
         Q.sub.n =M.sub.n if C.sub.n =1, Q.sub.n =M.sub.n -1 if C.sub.n =0 
    
     where C n  is a carry out bit indicative of the sign of the remainder (R n ). 
     An example of an apparatus for performing non-restoring division and embodying the foregoing principles is illustrated in FIG. 1. FIG. 1 depicts a fixed point binary divider 100. Data locations refer to the start of the nth iteration. The remainder from the previous iteration n-1 is latched into the remainder latch 102 of the carry propagate adder 104. The last carry (off the end of the remainder) is used by the quotient generator 106 to generate Qn-1, since Qn-1 = Mn-1 - Cn-1, where Cn-1 represents the last carry that occurred. Cn-1 indicates the sign of Rn-1 (1 if negative, 0 if positive) and is generated by counting carries out of the carry propagate adder 104. This covers the case where Qn-1 =Mn-1 -1. Mn-1 is represented by two&#39;s compliment form in the multiple latches 108. The quotient generator 106 is a two-bit down counter and binary trigger. 
     The last remainder Rn-1 wraps back on the carry propagate adder 104 through a two-bit wired left shift 110 to become PDn. Mn*D feeds the other side of the carry propagate adder from the multiple gates 112. The multiple gates form 1× or 2× divisor multiples in true or compliment form from the divisor register 114 as selected by the multiple select lines 116. The multiple select lines generate the extra carry into the adder (hot one) when a two&#39;s compliment divisor is selected. 
     The last remainder (left shifted by 2 bits) also feeds the ratio decoder adder 118 which resolves its high order bits, along the high order bits of Mn*D into the high order bits of Rn. The high order bits of Rn, shifted left by two bits to form PDn+1, feed two ratio decoders 120, 122 that select a positive and negative Mn+1 from the ratio of PDn+1 to the divisor D. The carry-out of the multiple decoder adder indicates the sign of PD n+1 , and is used to select the opposite signed Mn+1 from the multiple latch drivers 124. The selected Mn+1 is then latched into the quotient multiple latches 108 and is ready for the next iteration. 
     In the divider of FIG. 1, the sign of Rn-1 is formed by counting the carries out of the carry propagate adder with a binary trigger, and the sign of PDn+1 is formed by waiting for the carry out of the decoder adder 118. In any event, either method can be used as determined by the adder organization. The initial dividend is not shown in FIG. 3. A typical hardware saving location for the initial dividend is the quotient register 126 (by time-sharing). 
     As explained above, two ratio decoders are provided. A positive ratio decoder 120 and a negative ratio decoder 122. The two separate decoders are provided because the positive -nd negative regions are not completely symmetrical. That is to say, for a given divisor, the proper value of Mn where the partial dividend PD n  is positive will not necessarily be the same as where the partial dividend PD n  is of the same magnitude but negative. This principle is illustrated in the charts of FIGS. 2A and 2B. 
     Horizontally on each chart are plotted partial dividend values in sixteenths while divisor values are plotted vertically in sixteenths. The chart of FIG. 2A represents positive partial dividends and the chart of FIG. 2B represents negative partial dividends. 
     Within each chart there are four slanted lines referred to as exact &#34;boundaries.&#34; The exact boundaries 202-216 represent the four possible ratios of PDn/D which are of interest in decoding M n  and were taken from Table I. The crooked lines 218, 220 near the 2/3 and 5/3 exact boundaries represent the nearest integer ratio whose magnitude is less than or equal to the exact ratio. In the decoder adder 118, PD and D are represented to a bit position weight of 64 (thus the low order bit of PDn+1 as available to the decoder has a weight of sixteen). Thus each square on the chart represents a possible ratio between PD n+1  and D which can be seen by the ratio decoders . 
     The positive and negative regions as delimited by the integer boundaries are not symmetrical. The negative region really shows the 1&#39;s compliment form of the partial dividend and is therefore off by one bit. The boundary regions, however, where two multiples overlap are equal in the positive and negative region. 
     In the chart for the positive partial dividends, the point in the upper left corner of each square represents the bit patterns of PD n+1  and D, while the exact ratio of that particular PD n+1  to D is represented by any point within the square or on its upper or left boundary. 
     Overlap of multiple ranges for some values of PDn/D (see the bottom of FIG. 2) permits some flexibility in choosing the decode boundary for a particular multiple. However, much of the flexibility is lost because of the error introduced by ignoring the carry into the lowest bit position of PD n  in the decoder adder 118. For example, the positive decoder 120 for multiple zero must select on all bit patterns of PD n  and D as represented by squares to the left or cut by the one-third exact boundary. A line which is drawn through the right most extreme of these squares would be referred to as the one-third integer boundary. Because of the overlap in the range for selection of M n  =0 and M n  =1, the decoder for M n  =0 could select on any square between the one-third and two thirds boundaries. But because the carry-in error may permit PD n  to be low by one bit, the multiple zero decoder may not select on any square which is just to the left of the two thirds integer boundary. The dashed lines represent the left edge of those squares whose bit patterns are decoded to select M n  =1. The remaining squares in the upper range are then decoded to select M n  =2. 
     The negative ratio decoder 122 (the decoder for negative partial dividends) is derived in a similar manner. The truncation and carry-in errors in this case are toward the zero partial dividend so that the point at the upper left corner of each square represents the bit pattern seen by the decoder. The dashed lines represent the left edges of the squares selected for Mn=-1. The Mn=0 line is shown to imply the right edge for Mn=-1. 
     In the ratio decoders 120, 122 and the tables of FIG. 2, the variables are defined as divisor=0,1xyz and partial dividend=ab.cdef. 
     While the divider of FIG. 1 has provided a successful mechanism for performing non-restoring binary division it does have a number of features which are open for improvement. For example, having separate decoders for the positive and negative partial dividend regions does not make for an efficient integrated circuit real estate. Further, in some instances, the implementation of these decoders can create engineering limitations on the speed of division. A second part of the present application relates to the convert to binary function. Convert to binary (CVB) is an instruction that converts decimal digits expressed in binary form, into a binary number. For Example, a decimal number expressed in sixteen digits (15 representing the number, 1 representing the sign of the number) can be converted into a 32 bit binary word. 
     SUMMARY OF THE INVENTION 
     The inventors have discovered that multiple boundaries can be selected such that the positive and negative regions are symmetrical with only a small number of exceptions. Using these boundaries, an essentially symmetrical, unified ratio decoder was constructed using only about one-half of the integrated circuit real estate of conventional ratio decoder pairs. By decoding the sign bit from the ratio decoder adder, the ratio decoder can recognize the exceptional areas and handle them accordingly. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     The present invention will be better understood by reference to the drawings, wherein: 
     FIG. 1 is an illustration of the hardware organization of a prior art binary divider; 
     FIGS. 2A and 2B are charts illustrating partial dividend/divisor ratios, showing boundary regions for the ratio decoders. The chart of FIG. 2A represents positive partial dividends and the chart of FIG. 2B represents negative partial dividends. 
     FIG. 3 is an illustration of an improved binary divider having a symmetrical ratio decoder; 
     FIG. 4 is a chart illustrating the boundary regions for an embodiment of the symmetrical ratio decoders of FIGS. 3 and 7A/B; 
     FIG. 5 is a more detailed diagram of the ratio decoder adder and the exclusive OR gates of FIG. 3. 
     FIG. 6 is an illustration of the logic equations embodied in the symmetrical ratio decoders of FIGS. 3 and 7A/B; 
     FIGS. 7A and 7B illustrate an embodiment of an apparatus for performing, non-restoring division, which can generate four quotient bits per clock cycle. 
     FIG. 8 illustrates and embodiment of a convert to binary circuit suitable for sharing a common data path with the apparatus of FIG. 7A/B. 
     FIG. 9 illustrates another embodiment of a convert to binary circuit which can retire a 64 bit double word of decimal digits in four cycles. 
     Like components appearing in more than one figure are designated by like reference numerals. 
    
    
     DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     Described herein are A) an essentially symmetrical ratio decoder which symmetrically covers all areas in both the positive and negative regions with only a small number of exceptions; B) an improved divider using symmetrical ratio decoders; C) divide and convert to binary circuits using a common data path to halve execution time; and, D) a reduced execution time convert to binary circuit using carry save adders and carry propagate adders. 
     A. Symmetrical Ratio Decoder For Binary Division 
     The present section describes an essentially symmetrical ratio decoder which symmetrically covers all areas in both the positive and negative region with only a small number of noted exceptions. By using this essentially symmetrical ratio decoder, the need for separate positive and negative decoders is eliminated and a significant amount of integrated circuit real estate is saved in both the decoder and the binary divider. 
     FIG. 3 is an illustration of a binary divider having a symmetrical ratio decoder. Like the divider of FIG. 1, the present divider includes a divisor register 114, multiple gates 112, a carry propagate 104, a remainder latch 102, a two bit wire shift left 110 to form PDn from Rn-1, a ratio decoder adder 118, and a quotient register 126. These components operate in the same manner as the like numbered components described with respect to FIG. 1. 
     The apparatus of FIG. 3 assumes that at the start of clock cycle n, an initial remainder R n-1  is in the remainder latch 102, and an initial carry out and multiple (CRY n-1  and M n-1 ) stored in the multiple latches 308. Actual start up will be discussed in more detail later, with respect to the embodiment of FIGS. 7A/7B. 
     In contrast to the binary divider of FIG. 1, the present divider eliminates the positive and negative ratio decoders 120, 122 and the multiple latch drivers 124. Instead, the six lower order bits from the ratio decoder adder are provided to the Exclusive-OR gates 302, wherein each of the six bits is exclusive ORed with the the most significant bit (bit 0) from the ratio decoder adder 118. In this manner, the six lower order bits of the sum S&#39; from the ratio decoder adder 118 are fed to the ratio decoder 304 in true form when the MSB is zero (positive remainder) and in 1&#39;s compliment form when the MSB is a one (negative remainder). Throughout the remainder of this specification the most significant bit (MSB) of the result from any ratio decoder adder will be referred to as sumbit0. 
     In addition to receiving the output of the Exclusive-OR gates (the lower order six bits of S&#39; or the 1&#39;s compliment thereof), the symmetrical ratio decoder 304 receives the divisor D and sumbit0 from the ratio decoder adder 118. It should be understood that the symmetrical ratio decoder 304 of FIG. 3 is not simply a combination of the positive and negative decoders 120, 122 of FIG. 1. While such a combination could be achieved by merely combining the positive and negative region decode logic into a single large decoder and additionally decoding the most significant bit from the ratio decoder adder, this alone would not accomplish the goal of saving circuitry and integrated circuit real estate. 
     Advantageously, the symmetrical decoder of FIG. 3 uses a single combined region, defined by appropriately choosing the multiple boundaries, to handle both positive and negative partial dividend values. By using the most significant bit from the ratio decoder adder to 1&#39;s compliment negative partial dividends, the symmetrical ratio decoder 304 decodes all partial dividends as though they were positive and uses the most significant bit from the ratio decoder adder to resolve the ambiguous cases. The carry out from the carry propagate adder 104 can be used to select whether the M n  *D result is to be added to or subtracted from the divisor (i.e. no carry=add, carry=subtract). 
     The operation of the symmetrical ratio decoder of FIG. 3 will be better understood by reference to FIG. 4. FIG. 4 is a combined decode chart for both positive and negative ratios. In FIG. 4, the four slanted lines 402-408 represent, respectively, the integer boundaries for the M n  =0 . . . M n  =2 regions. The multiple values are designated in shorthand form, wherein M n  =0 is designated M0, M n  =1 is designated M1 and M n  =2 is designated M2. The two crooked lines 410, 412, represent the boundaries selected by the inventors to achieve approximate symmetry. Specifically, the first crooked line 410, designates the selected boundary between M n  =0 and M n  =1. Similarly, the second crooked line 412, designates the selected boundary between M n  =1 and M n  =2. 
     By selecting the boundary regions as illustrated in FIG. 4, the inventors have configured the combined decode chart such that there are only five ambiguous decode ratios (two in the M n  =1 region and three in the Mn=2 region). These ambiguous ratios (designated by reference numerals 414-422) are recognized by the decoder 304 and handled appropriately by reference to the most significant bit from the output of the ratio decoder adder (sumbit0). Specifically, two of the areas 414, 416 in the M n  =1 region will decode Mn=0 only if they are partial dividends that were made positive by 1&#39;s complimenting (sumbit0=1). Otherwise, these areas 414, 416 will decode as M n  =1. Further, three areas 418, 420, 422 in the M n  =1 region will decode M n  =2 only if they are partial dividends that were not 1&#39;s complimented (sumbit0=0). Otherwise, these three areas will decode as M n  =1. 
     As an example, assume that the ratio decoder adder 118 (FIG. 2) has just subtracted a partial divisor of 8 (M n-1  =1, D=00001000 binary) from a partial dividend of 04 (00000100 binary). The ratio decoder 118 would accomplish the subtraction by adding the 1&#39;s compliment of the partial divisor to the partial dividend as illustrated below: ##EQU2## The six lower order bits of the result are sent to the XOR gates 302 where each bit is exclusively OR&#39;ed with bit 0 from the ratio decoder adder. In this case, sumbit0 is a one, thus the result is 1&#39;s complimented and sent to the decoder as 00000100. 
     Turning again to FIG. 4, it will be observed that where the partial divisor is 1000, and six lower order bits (abcdef) of the partial dividend are 000100, the multiple M n  for the next iteration could be either 1 or 0. By looking at sumbit0 from the output of ratio decoder adder 118, the ratio decoder establishes that the partial dividend became positive by taking the 1&#39;s compliment. Thus, the value M n  =0 is output as a result of the decode. Bit 1 is not needed because the result shifted left by 2 (SL2) is input the decoder 304. 
     FIG. 5 is a more detailed diagram of an embodiment of the adder and XOR sections of FIG. 3. As is illustrated in FIG. 5, where an eight bit adder is used as the radio decoder adder 118, bit 1 is not fed to the ratio decoder, and bits 2 through 7 are individually exclusive OR&#39;ed with sumbit0 before being sent to the ratio decoder. 
     FIG. 6 shows the logic equations embodied in the ratio decoder 304 where the partial remainder (the output of the XOR gates) is of the form abcdef and the divisor is of the form 1xyz. Sumbit0=0 indicates positive sum, while sumbit0=1 indicates a negative sign. 
     The operation of the embodiment of FIG. 3 will now be described in more detail. Again, we will assume that at the start of clock cycle n, an initial remainder Rn-1 is held in the remainder latch 102, and an initial carry out CRY n-1  and multiple M n-1  is held in the multiple latches 308. For purposes of the example, we will also assume a 34 bit initial remainder and a 32 bit divisor. 
     At the beginning of cycle n, the divisor D (from the divisor register 114) is applied to the multiple gates 312. The multiple gates 112 form 1X or 2X divisor multiples in true or compliment form as selected by the multiple select lines 316. The multiple select lines 316 carry the multiple M n-1  and the carry out CRY n-1  from the previous cycle. A carry out of one (CRY n-1  =1) causes the multiple gates 112 to output the 1&#39;s compliment of M n-1  * D. A no carry (CRY n-1  =0) causes the multiple gates 112 to output M n-1  * D in true form. 
     The M n-1  * D (in true or compliment form, as output from the multiple gates 112) is provided, in parallel, to the carry propagate adder 104 and to the ratio decoder adder 118. The carry propagate adder 104 forms the sum of the partial dividend PD n  and the M n-1  * D value output from the multiple gates. The CRY n-1  (from the multiple select lines) generates a hot 1 into the CPA 104 when a complimented divisor multiple is selected (CRY n-1  =1). The resulting remainder Rn is latched into the remainder latch 102. As illustrated in FIG. 3, the partial dividend PD n  is formed by wire shifting R n-1  to the left by two bit positions. 
     In parallel with the CPA 104, the ratio decoder adder forms the sum of the eight lower order bits of the partial dividend PD n  and the M n-1  * D value output from the multiple gates. The MSB (bit 0) of the sum is input to the XOR gates 302 and the symmetrical ratio decoder 304 which operate, as described above, to produce a multiple value M n . The M n  value, so generated is stored, along with the carry out CRY n  from the CPA 104, in the multiple latches 308. The M n  value, the carry out CRY n , and sumbit 0 (from the ratio decoder) adder are also provided to the quotient generator 306. 
     Like the quotient generator 106 of FIG. 1, the quotient generator 306 of FIG. 3 uses the carry out CRY n  from the carry propagate adder 104 to determine the quotient bits from the decoded multiple M n . However, in the apparatus of FIG. 3, the symmetrical ratio decoder 304 provides only an absolute value of the decoded multiple. Thus, for example, where the result from the ratio decoder adder is negative, and the decoded multiple is M1, the ratio decoder will output M n  =1 (binary 01) whereas in fact, the proper multiple is M n  =-1 (binary 11). 
     To compensate for the fact that the decode multiple is provided in absolute value form, sumbit0 (sum bit0) from the ratio decoder adder is provided to the quotient generator 306. Since sumbit0 indicates the actual sign of the decoded multiple (sumbit0=1 indicates a negative multiple, sumbit0=0 indicates a positive multiple), the quotient generator uses this bit to adjust the decoded multiple value to reflect its proper sign. This is readily accomplished by 2&#39;s complimenting the decoded multiple when sumbit0=1. The carry out CRY n  from the carry propagate adder 104 determines whether the quotient generated by the quotient generator is equal to the multiple M n  or the multiple minus 1 (M n  -1). Where the carry out is equal to 1, the quotient Q n  =(M n  -1). Where the carry out CRY n  is equal to 0 (no carry) then Q n  =M n . 
     Once determined, the quotient (2-bits) is put away in the quotient register 126 which fills up starting at the least significant two bits. 
     It should be understood that the foregoing principles can be used to devise symmetrical ratio decoders which generate more than two bits per decode. In such embodiments, the number of multiple regions would be increased as would the number of bits to be resolved by the decoder. 
     Improved Divider Using Symmetrical Ratio Decoders 
     Advantageously, the symmetrical ratio decoder defined by the equations of FIG. 6 can be used in conjunction with an improved divider circuit which can retire 4 bits of the quotient in each iteration. Such a circuit is illustrated in FIG. 7. 
     The operation of the apparatus of FIG. 7 assumes a start up phase wherein a 32 bit divisor is made positive and normalized to the form 001XX . . . X. The Divisor register W-REG) 702 holds the normalized divisor. A significant bit overflow trigger 704 holds the least significant bit (bit 31) of the original divisor in cases where the divisor has been normalized by a right shift of 1. For example, where the original divisor is 01XX . . . 01; a right shift of 1 is performed to normalize to the form 001XX . . . X and the overflow trigger is set to 1. 
     As an additional part of the start up phase, a 64 bit fixed point dividend is made positive and normalized (i.e. shifted by the same amount and in the same direction as the divisor). The 32 higher order bits of the dividend are held in the High Order Dividend register (H-REG) 706. The low order 32 bits of the dividend are held in the Low Order Dividend register (L-REG) 710. The H-REG and L-REG each include two overflow triggers 708, 712. The L-REG overflow triggers 712 are used during start up when the divisor is the maximum negative number and requires a right shift of two, or when the divisor is a positive number of the form 01XX . . . X and requires a right shift of one. The H-REG overflow triggers 708 are used to hold the low order 2 bits from CPA2 728, thus making the H-REG 706,708 effectively a 34 bit register. 
     Once initialized, the apparatus of FIG. 7 commences generation of the quotient at the rate of 4 bits (2 pairs) per iteration. The initial quotient pair is generated by a first quotient generator (Qn-GEN) 714. To generate the initial quotient pair, the multiple M n  is decoded in a first symmetrical ratio decoder 716 from H-REG bits 2-7 and from W-REG bits 3-5. A first set of multiple gates 717 provides any of the 2&#39;s complimented divisor, the 2&#39;s complimented divisor shifted left 1 (SL1), or the 2&#39;s compliment of zero to a first 34 bit CPA (CPA1) 718 depending on the value of M n  provided by the M n  decoder 716. The first 34 bit CPA then adds the value so provided to the shifted left 2 (SL2) normalized dividend. 
     The specific relationship between Mn and the operation of the 34 bit carry propagate adder 718 is illustrated in Table III, below: 
     
                       TABLE III______________________________________Mn        Operation of 32 bit CPA1______________________________________0         subtract 2&#39;s compliment of 0 (forces carry     out CRYn from CPA1&#39; 718)1         subtract divisor2         subtract divisor shifted left one.______________________________________ 
    
     It should be understood that during cycles, other than the first, the multiple gates 717, 725 can also provide the the complimented divisor or the complimented divisor SL1 when the carry CRY n+1  =0. However, because a subtraction must occur on the first cycle, a carry is assumed (for the first cycle only). Thus, this factor is not considered in Table III. 
     The carry out (CRYn) from CPA1 718 and the most significant bit of the result (sumbit0) from an eight bit carry propagate adder (CPA2&#39;) 720 are used by quotient generator 714 to determine the first two bits of the quotient from the decoded multiple. As explained with reference to the embodiment of FIG. 3, sumbit0 is indicative of the actual sign of the multiple (which is provided only in absolute form by the symmetrical ratio decoders). 
     For the determination of the initial two quotient bits, sumbit0 is set to 0. This is because CPA2&#39; 720 does not lay a role in the determination of these bits and because the first multiple M n  will always be positive by virtue of the fact the normalized dividend is initially made positive. For subsequent cycles, sumbit0 is latched from the 8 bit adder 720 into the Mn+2 decoder/latches 730 and fed back into the first quotient generator 714. The generation of quotient bits by the first quotient generator 714 is illustrated in Table IV below: 
     
                       TABLE IV______________________________________Decoded Multiple         Generated Quotient Bits______________________________________Where, CRY.sub.n =1 (carry out) and sumbit0=0:M.sub.n =0    Q.sub.n =00M.sub.n =1    Q.sub.n =01M.sub.n =2    Q.sub.n =10Where, CRY.sub.n =0 (no carry) and sumbit0=0:M.sub.n =0    Q.sub.n =11M.sub.n =1    Q.sub.n =00M.sub.n =2    Q.sub.n =01Where, CRY.sub.n =1 and sumbit0=1:M.sub.n =0    Q.sub.n =00M.sub.n =1    Q.sub.n =11M.sub.n =2    Q.sub.n =10Where, CRY.sub.n =0 and sumbit0=1:M.sub.n =0    Q.sub.n =11M.sub.n =1    Q.sub.n =10M.sub.n =2    Q.sub.n =01______________________________________ 
    
     In parallel with the operation of CPA1 718, an 8 bit carry propagate adder (CPA1&#39;) 724 subtracts from the SL2 high order 8 bits of the dividend by adding to it, the 1&#39;s compliment or SL1 1&#39;s compliment of the high order 8 bits of the divisor (from the W-REG 702). Again the proper value for presentation to the adder 720 is selected by the M n  decoder 716 which provides a select input to a second set of multiple gates 725. Sum bits 2 through 7 out of CPA1&#39; 724 represent an approximate t1D 20 partial dividend PD&#39;. Sum bit 0 (sumbit0) is the most significant bit out of CPA1&#39; and represents the sign of the result. 
     Sumbit0 out of CPA1&#39; 720 is exclusive OR&#39;ed (at the XOR gates 722) with bits 2 through 7 from CPA1&#39; 724. As described with reference to FIG. 5, the XOR gates determine whether these bits are sent to the decoder in true or 1&#39;s compliment form. Sumbit0=1 indicates that sum bits 2:7 out of the first eight bit CPA 724 need to be ones complimented before being used by a second multiple decoder (the Mn+1 decoder) 726. Sumbit0=0 out of CPA1&#39; 724 indicates that sum bits 2 through 7 can be used as they are by the Mn+1 decoder 724. High order bits 3 through 5 of the divisor are also provided to the multiple decoder 724 from the W-REG 702 (PD&#39;/D&#39; where D&#39; is the partial divisor). 
     The multiple generated by the Mn+1 decoder 726 and the carry out of CPA1 718 (CRYn), are input to a third set of multiple gates 727, where they select any of the true, SL1 true, or the 240 s compliment of the divisor or SL1 divisor for provision to CPA2 728. CPA2 728 adds the value so provided from the SL2 remainder from CPA1 718. 
     The operation of CPA2 is described in Table V, below: 
     
                       TABLE V______________________________________Mn            CRYn     Operation of 32 bit CPA2______________________________________M.sub.n =0 AND     CRY.sub.n =1                  PD + 2&#39;s compliment of 0 (forced                  carry)M.sub.n =0 AND     CRY.sub.n =0                  PD + 0M.sub.n =1 AND     CRY.sub.n =1                  PD + 2&#39;s compliment of DivisorM.sub.n =1 AND     CRY.sub.n =0                  PD + DivisorM.sub.n =2 AND     CRY.sub.n =1                  PD + SL1 2&#39;s compliment of DivisorM.sub.n =2 AND     CRY.sub.n =0                  PD + SL1 Divisor______________________________________ (CRY.sub.n =1 indicates a carry, CRY.sub.n =0 indicates no carry) 
    
     The multiple generated by the Mn+1 decoder 726 also combines with CRY n+1  out of the 34 bit CPA2 728 at a second quotient generator (Qn+1 GEN) 723, which generates the second quotient pair using the previously described rules. The contents of the L-REG 710, 712 are then shifted left by four (SL4) and the four quotient bits are loaded into the vacated 4 low order bit portions of the register. The 34 bit remainder out of CPA2 728 is fed to the H-REG 706,708, to be used in the next cycle. 
     In parallel with the operation of CPA2 728, CPA2&#39; 720 takes the high order 8 bits of the remainder SL2 out of CPA1 718 and adds the high order 8 bits of the W-REG 702 true or SL1 true or complimented or SL1 compliment in accordance with multiple generated by the Mn+1 decoder 726. Once again, the multiple selected by the Mn+1 decoder 726 is provided to CPA2&#39; 720 by a fourth set of multiple gates 729. 
     Sum bits 2 through 7 out of CPA2&#39; 720 represent an approximate partial dividend PD&#39;; sum bit 0 represents the sign bit. As described with reference to FIG. 5, a second set of exclusive or gates 732 use sumbit0 to correct for the fact that the multiples from the Mn+2 decoder are provided only in absolute form. Again, sumbit0=1 out of 8 bit CPA2&#39; 720 indicates that sum bits 2 though 7 out of CPA2&#39; 720 need to be 1&#39;s complimented before being used by a third multiple decoder- 730 (the Mn+2 decoder). Sumbit0=0 out of CPA2&#39; 720 indicates that sum bits through 7 out of CPA2&#39; 720 can be used as they are by the Mn+2 decoder 730. High order bits 3 through 5 of the divisor (from the W-REG 702) are also provided to the Mn+2 decoder 730 in order to enable it to generate the next multiple. 
     The multiple generated by the Mn+2 decoder 730, bit0 of the sum (sumbit0) from CPA2&#39; 730, and the carry out (CRY n+1 ) from CPA2 728 are latched up in the Mn+2 decoder latches 731 to be used in the next cycle. The multiple latched in the Mn+2 decoder 730 and the latched CRYn+1 will determine to either add the true divisor, SL1 true divisor, 2&#39;s compliment divisor, or SL1 2&#39;s compliment divisor to the SL2 remainder from H-REG 706, 708 for the next divide iteration. 
     The first quotient pair in the next divide iteration and the following iterative cycles is determined from the latched multiple and the latched sumbit0 (as latched in the Mn+2 decoder latches 731) and the carry out CRY n  of CPA1 718. 
     As an alternative to loading the quotient bits into vacated potions of the L-REG 710, 712, the quotient can be loaded into a separate quotient register. As is conventional, the register which holds the quotient can be provided with logic to detect fixed point divide exceptions, which are, in turn, reported to the system by way of an interrupt. 
     Divide and CVB Using Common Data Path to Halve Execution Time 
     Advantageously, the two cascaded 34 bit adders 718, 728 of FIG. 7 can be shared with a convert to binary (CVB) circuit. By using a common data path for the divide and CVB instructions a significant amount of chip logic and real estate can be saved. Further, the number of chip crossings, along with respective time loss, can be reduced. Advantageously, the use of the two cascaded adders cuts in half the execution time of CVB (from 16 to 8 cycles) and cuts the execution time of the divide (from 28 to 13 cycles). 
     The convert to binary instruction will now be explained by reference to FIG. 8. Convert to binary (CVB) is an instruction that converts decimal digits expressed in binary form, into a binary number. For example, a decimal number expressed in sixteen digits (15  representing the number, 1 representing the sign of the number) can be converted into a 32 bit binary word. 
     The high order 32 bit word 802 of a double word of decimal digits are provided to the CVB circuit from a general purpose register. In the high order 32 bit word 802, 8 decimal digits are each represented by 4 bits. In the lower order 32 bit word (not shown), 7 decimal digits are represented by 4 bits each and the lower order 4 bits represent the sign of the decimal number. 
     As illustrated in FIG. 8, the high order decimal digit (A) defined by bits 0-3 of the high order 32 bit word is decoded, by a first decoder 804, and the results of the decode are sent to CPA1 718. A second decoder 806 decodes the second decimal digit (B), defined by bits 4-7 of the high order 32 bit word, and sends the results of the decode to CPA2 728 (into the positions vacated by the SL1 and SL3 of the output from CPA1 718). The output from CPA2, which is the binary number of the first two converted decimal digits, is then latched into the W-REG 702. 
     The conversion continues by wire shifting the contents of the W-REG 702 left by one (SL1) and left 3 (SL3) to CPA1 and adding the decodes of the next decimal digits into the vacated bit positions of the respective carry propagate adders. The SL1 and SL3 addition of the converted number constitutes a multiplication by 10. 
     The most significant bit (bit 0) of each decimal digit is gated directly to the left side of the corresponding carry propagate adder 718, 728 (e.g. CPA1 718 receives bit A0 of decimal digit A and CPA2 receives bit B0 of decimal digit B). The decoders 804, 806 produce the remaining three bits of each digit from the 4  original bits and gates them to the right side of the corresponding carry propagate adder. Where the decimal digit is an 8 (1000 bin), the decoder outputs &#34;111&#34; for bits 1-3 e.g. A1--3 or B1-B3). Where the decimal digit is a &#34;9&#34; (1001 bin), the decoder outputs &#34;111&#34; (the same as for decimal digit 8) and also adds a hot 1 to the corresponding carry propagate adder. The lower order three bits of all other decimal numbers (0000-0111 binary) are gated through to the carry propagate adders, from the decoders, in their original form. 
     The least significant decimal digit (LSD) in the double word indicates the sign of the decimal number. A negative number is indicated by a hexidecimal digit value of B or D A hexidecimal digit value A, C, E or F indicates a positive number. Circuitry can also be added to signal a data exception when the least significant digit is less then 10 (A hex.). For a negative number (LSD=B or D) the result from CPA1 is provided to CPA2 in 2&#39;s compliment form. Where the decimal number is positive LSD=A, C, E or F) the result from CPA1 is provided to CPA2 in complement form. 
     It should be understood that in the above-described embodiment, decimal digits other than the LSD should never be greater then 9. Circuitry can also be added to signal a data exception when this condition occurs (i.e. a digit, other than the LSD, is greater than 9). 
     Using two cascaded carry propagate adders enables conversion of two decimal digits per cycle (8 cycles for a decimal number expressed in 16 digits). 
     Reduced Execution Time Convert to Binary 
     Another embodiment of a convert to binary circuit which reduces the execution time of a CVB operation to 4 cycles is illustrated in FIG. 9. Like the circuit of FIG. 8, the circuit of FIG. 9 converts a 15 digit+1 sign digit decimal number to binary form, examining the decimal digits from left to right (most significant to least significant). 
     The apparatus of FIG. 9 converts a first pair of decimal digits in the double word through a first carry save added 902 and a first carry propagate adder 904, and converts a second pair of decimal digits in the double word through a second CSA/CPA pair 906, 908 before the converted number is latched up in a register (W-REG) 910. In FIG. 9 the decimal digits in each group of four (two pairs) are represented by letters A through D. 
     Like the W-REG 702 of FIG. 8, the W-REG 910 is a 32 bit register. In FIG. 9, the 32 bits of the W-REG 910 are indicated by W0-W31 (with W0 being the MSB). In order to have access to the correct bits of four decimal digits at a time and the correct hot one values (HA-HD), the circuit of FIG. 9 uses four decoders 912-918 which operate in a similar manner to the decoders 804, 806 of the embodiment of FIG. 8. 
     Each of the carry save adders 902, 906 comprises four 4-2 CSAs (920-926 and 932-938 respectively) and twenty eight 3-2 CSA (of the type designated by reference numerals 928, 930, 940, 942). The 4-2 CSAs handle addition for the first four columns of addition (as described below). The 3-2 CSAs handle the addition for the remaining columns. An example of a 4-2 CSA and a single level CSA three is illustrated in IBM Technical Disclosure Bulletin Vol. 23, No. 8, January 1989, Pp. 3811-3814, entitled &#34;4-2 Carry-Save Adder Module&#34;, which is incorporated by reference. 
     The CVB method used by the apparatus of FIG. 9 is similar to that of FIG. 8 except that more quantities are added to get a binary result. As with the CVB circuit of FIG. 8, the first converted binary number (generated by CPA1 718 in the embodiment of FIG. 8) is defined by formula 1, as follows: 
     
         ______________________________________(formula 1)______________________________________   W3 . . . W30               W31    A1     A2   A3   W1 . . . W28               W29    W30    W31  A0+                                  HA   FIRST CONVERTED NUMBER______________________________________ 
    
     Further, like CPA1/CPA2 718, 728, of FIG. 8, the first CASA/CPA pair 902, 904 of the embodiment of FIG. 9 generates the first two converted numbers as follows: 
     
         ______________________________________(formula 2)______________________________________  (FIRST CONVERTED NUMBER) B1 B2                           B3  (FIRST CONVERTED NUMBER) B0+                           HB(FIRST AND SECOND CONVERTED NUMBER)______________________________________ 
    
     by substitution of formula 1 for the first converted number, formula 2 becomes: 
     
         ______________________________________(formula 3)______________________________________W3 . . . W30 W31 A1                 A2     A3   B1   B2   B3W1 . . . W28 W29 W30                 W31    A0+                        HA+W3 . . . . . . W30                 W31    A1   A2   A3   B0+W1 . . . . . . W28                 W29    W30  W31  A0+                                  HA+                                       HB(FIRST AND SECOND CONVERTED NUMBER)______________________________________ 
    
     For digit A, SL1 and SL3 of the W-REG 910 and the correct bits of digit A from the first decoder 912 and HA from the decoder 912 are added together. For digit B, SL1 and SL3 of the first converted digit A and the correct bits of digit B from the second decoder 914 and HB from the decoder 914 are added together. 
     To make the addition more efficient, the hot 1 (HA) from the first digit is moved to the first column and three HAs are added to row 2. Also, an HA is added to row 5 (see below). 
     
         ______________________________________COLUMN8       7      6      5    4    3    2    1    ROW______________________________________. . . W30   W31    A1     A2   A3   B1   B2   B3   1. . . W28   W29    W30    W31  A0   HA   HA   HA   2+                                     HA   3+. . . W28   W29    W30    W31  A1   A2   A3   B0   4+. . . W26   W27    W28    W29  W30  W31  A0   HA   5+                                     HA   6+                                     HB   7(FIRST 2 DECIMAL NUMBERS CONVERTED TOBINARY)______________________________________ 
    
     To accomplish the above addition, a 4-2 CSA 920-926 is used for each of the first 4 columns and a 3-2 CSA 928, 930 is used for each column after the 4th. Column 1 is added by a 4-2CSA 920. The five inputs are are rowl through row 5. Row 6 is added in bit position 31 of the left side of CPA1 904. Row 7 is added as the carry in (hot 1) to CPA1 904. 
     One row is eliminated after column 4 since row 2 and row 4 are equal at that point. Row 2 and row 4 can be be combined into one row (starting at column 5) if from column 5 the bits are shifted left by one position (equivalent to doubling). 
     In FIG. 9, the first Carry Save Adder 902 adds the respective columns to produce a sum and a carry. The first carry propagate adder 904 adds the sums and carries from the first carry save adder 902. 
     The above described process continues for the second pair of decimal digits (C,D), as the output X-bus from CPA1 replaces the W-bits with X-Bits for use by the second carry save adder 906. Similarly, in the second CSA/CPA pair, the A-digit is replaced by the C-digit and B-digit is replaced by D-digit. The sum out of CPA2 908 is latched in the W-REG, to be used in the next cycle wherein the next two pairs of decimal digits are converted. 
     When the last 4 digits ABCD in the doubleword are decoded, the conversion proceeds differently. The A and B digits are converted (as before) through the first CSA 902 and the first CPA 904. Digit C is the last data digit to be converted. Digit C is converted by taking the output of the first CPA 904 and shifting it left 1 and left 3 through the second CPA 908. The decode for digit C is then inserted into the corresponding vacated bit positions (as was done in the embodiment of FIG. 8 with CPA2 728, for example). The second CSA 906 does not participate. 
     The last digit of the doubleword is the sign digit. If the sign digit is positive (i.e. not hex B and not hex C) the output of the second CPA 908 is the final result and put away in the general purpose register. If the sign digit is negative, the output of the second CPA 908 is put into the W-REG 910. An extra cycle is added to 2&#39;s compliment the contents of the W-REG 910 (via the second CPA 910) before the resulting signed converted number is sent to the general purpose register. 
     Many variations and modifications which do not depart from the scope and spirit of the invention will now become apparent to those of skill in the art. Thus, it should be understood that the above described embodiments have been provided by way of example rather than as a limitation.