Abstract:
A method and system for transmitting bit streams in a telecommunication system, by combining a bit stream with a first portion of a preamble, applying power loading to the combined bit stream, applying eigen-steering to the power loaded bit stream, and combining a second portion of the preamble with the eigen-steered bit stream for transmission. The first portion of the preamble includes an HT preamble, and the second portion of the preamble includes a legacy preamble.

Description:
FIELD OF THE INVENTION  
       [0001]     The present invention relates generally to data communication, and more particularly, to data communication in multi-channel communication system such as multiple-input multiple-output (MIMO) systems.  
       BACKGROUND OF THE INVENTION  
       [0002]     A multiple-input-multiple-output (MIMO) communication system employs multiple transmit antennas in a transmitter and multiple receive antennas in a receiver for data transmission. A MIMO channel formed by the transmit and receive antennas may be decomposed into independent channels, wherein each channel is a spatial sub-channel (or a transmission channel) of the MIMO channel and corresponds to a dimension. The MIMO system can provide improved performance (e.g., increased transmission capacity) if the additional dimensionalities created by the multiple transmit and receive antennas are utilized.  
         [0003]     MIMO techniques are adopted in wireless standards, such as IEEE802.11n, for high data rate services. In a wireless MIMO system, multiple antennas are used in both transmitter and receiver, wherein each transmit antenna can transmit a different data stream into the wireless channels whereby the overall transmission rate is increased.  
         [0004]     There are two types of MIMO systems, known as open-loop and closed-loop. In an open-loop MIMO system, the MIMO transmitter has no prior knowledge of the channel condition (i.e., channel state information). As such, space-time coding techniques are usually implemented in the transmitter to combat fading channels. In a closed-loop system, the channel state information (CSI) can be fed back to the transmitter from the receiver, wherein some pre-processing can be performed at the transmitter in order to separate the transmitted data streams at the receiver side.  
         [0005]     Such techniques are referred to as beamforming techniques, which provide better performance in desired receiver&#39;s directions and suppress the transmit power in other directions. In fact, beamforming techniques are considered as promising candidates for IEEE 802.11n (high throughput WLAN) standard. In such a system, impairments such as channel estimation errors and frequency offset errors will degrade the system performance significantly. As such, there is a need for a beamforming transceiver architecture which performs processing on the preamble at the transmitter to reduce performance degradation due to the above impairments.  
       BRIEF SUMMARY OF THE INVENTION  
       [0006]     In one embodiment the present invention provides a beamforming transceiver architecture with enhanced channel estimation and frequency offset estimation capabilities in high throughput WLAN systems.  
         [0007]     Accordingly, in one example, the present invention provides a method and system for transmitting bit streams in a telecommunication system, by combining a bit stream with a first portion of a preamble, applying power loading to the combined bit stream, applying eigen-steering to the power loaded bit stream, and combining a second portion of the preamble with the eigen-steered bit stream for transmission. The first portion of the preamble includes an HT preamble, and the second portion of the preamble includes a legacy preamble.  
         [0008]     The present invention further provides a method and system for receiving the transmission in a receiver that implements: coarse AGC and frequency offset estimation based on the legacy preamble, and fine AGC and frequency offset estimation based on the HT preamble.  
         [0009]     These and other features, aspects and advantages of the present invention will become understood with reference to the following description, appended claims and accompanying figures. 
     
    
     BRIEF DESCRIPTION OF THE DRAWINGS  
       [0010]      FIG. 1  shows an example block diagram of a beamforming transmitter according to an embodiment of the present invention.  
         [0011]      FIG. 2  shows an example block diagram of an embodiment of a beamforming receiver according to the present invention.  
         [0012]      FIG. 3  shows the structure of the high throughput (HT) preamble format. 
     
    
     DETAILED DESCRIPTION OF THE INVENTION  
       [0013]     Under the IEEE 802.11n standard, the transmission of the preamble is in two portions for beamforming mode. The legacy part is transmitted without pre-coding (eigen steering) and the HT (high throughput) part, that uses the same data path as payload, is eigen-steered. In general, the coarse AGC (automatic gain control) and coarse synchronization is achieved through the legacy part for 802.11n systems. An example system is described in S.A. Mutjaba, “TGn Sync Proposal Technical Specification,” a contribution to IEEE 802.11-04-889r2, January 2005, (incorporated herein by reference).  
         [0014]     Because there is no pre-coding operation on the legacy portion of the preamble in beamforming systems, all the operations, such as coarse AGC and coarse synchronization, can be performed in the time domain, identical to the 802.11a system. For the MIMO part, the HT-STF (High Throughput Short Training Field) is used for fine AGC tuning and HT-LTF (High Throughput Long Training Field) is used for fine synchronization and MIMO channel estimation. Because pre-coding is applied to the HT part of preamble, fine synchronization and MIMO channel estimation need to be performed after post-coding operation at the receiver.  
         [0015]     However, in a beamforming system, the MIMO channels are decomposed into several independent channels with the associated eigenvalues of the channel covariance matrix. In general, the receive SNR in each decomposed channel is different because the eigenvalues associated with the decomposed channels are different from each other. Therefore, the frequency offset estimation errors and channel estimation errors will become large when the channel eigenvalues are relatively small.  
         [0016]     In other words, the operating SNR at each decomposed channel is different when performing channel estimation and frequency offset estimation. This will degrade the system performance because a packet will be considered as an error packet if any stream contributes to error bits, due to the imperfect frequency offset estimation and channel estimation. This is not the case for the basic MIMO operations because the received power variance among streams will be within a few dBs.  
         [0017]     As such, in one embodiment the present invention provides a beamforming transceiver architecture with enhanced channel estimation and frequency offset estimation capabilities in high throughput WLAN systems. The beamforming transceiver architecture performs processing on the preamble at the transmitter to reduce performance degradation due to the above-mentioned impairments.  
         [0018]      FIG. 1  shows an example block diagram of an embodiment of a transmitter  100  in a beamforming system, according to the present invention. The transmitter comprises multiple data stream processing paths for data streams S 1  . . . N ss , corresponding to transmit antennas  101  (i.e., TX 1  . . . TX Nt ). Each data stream processing path includes: a first combiner  102 , a multiplier  104 , an eigen-steering operation V  106 , and a second combiner  108 .  
         [0019]     In each data stream processing path, the power loadings P are applied to HT preamble together with the data streams. The antenna transmission power loading for each channel can be selected based on channel condition.  
         [0020]     As shown in  FIG. 1 , the coded data streams S i , i=1, . . . , N ss , are combined in the first combiners  102  with HT part of preamble, by padding the preamble to the beginning of the data streams. As described earlier, the HT-preamble portion is used for fine AGC, fine frequency offset estimation, and MIMO channel estimation. Each data stream along with the HT preamble is then adjusted on the power level P i , i=1, . . . , N ss , by multiplying the power loadings P i  in the multipliers  104  before being passed to the eigen-steering operation V  106 . The output of the eigen-steering operation is then combined with the legacy preamble in the combiners  108 , by padding the legacy preamble to the output of the eigen-steering operation, to generate X (i.e., the transmitted signal or HT portion of preamble) (e.g., X l . . .  X Nt ).  
         [0021]     X, the transmitted signal or HT part of preamble, can be expressed as:
 
X=VPS  (1)
 
         [0022]     where X is N t ×1; V (i.e., eigen-steering matrix at the transmitter) is N t ×N ss ; P is a N ss ×N ss  diagonal matrix and S (i.e., coded data streams) is N ss ×1. There are a number of algorithms for power loading computations, such as water-filling algorithms, reverse water-filling algorithms, etc. The eigen-steering matrix V is computed from the right singular matrix of the channel matrix H as:
 
H=UDV H   (2)
 
         [0023]     The above representation of H is the singular valued decomposition (SVD) of H, wherein U comprises a N_r×N ss  matrix which is used as a steering matrix at the receiver (e.g.,  FIG. 2 ). Further, D comprises a N ss ×N ss  diagonal matrix with channel eigenvalues along the diagonal and (•) H  is the Hermitian operation. With N r  receive antennas at a receiver (e.g., receiver  200 ,  FIG. 2 ), the channel H is a N r ×N t  matrix. With the additive noise at the receiver, the received signal can be expressed as:
 
 Y=HX+n=UDV   H    ·VPS+n=UDPS+n={tilde over (H)}S+n   (3)
 
 where
 
 {tilde over (H)}=U ( DP ) =UD′   (4)
 
 and n represents noise. 
 
         [0024]     Relation (3) above can be considered as the equivalent input-output relation with the equivalent channel {tilde over (H)}. Since both D and P are diagonal matrices, the product of D and P, or equivalently D′, is also a diagonal matrix. Therefore, the matrix U and D′ can be computed by U-D decomposing the matrix{tilde over (H)}. For HT preamble, relation (3) is still valid with the replacement of S by the HT preamble symbols, since the HT preamble goes through the same coding chain as the data streams. Therefore, the estimated channel based on the received HT preamble is {tilde over (H)}.  
         [0025]      FIG. 2  shows the block diagram of a receiver  200  in a beamforming system, according to the present invention described above. The receiver  200  processes data streams for N r  receive antennas  201  (e.g., RX 1 , . . . RX Nr ). The receiver  200  comprises coarse AGC and frequency offset estimation unit  202 , fine AGC and frequency offset estimation unit  204 , channel estimation unit  206 , U-D decomposition unit  208 , U H  operation unit  210  and D′ −1  operation unit  212 . First the coarse AGC unit  202  performs coarse AGC and synchronization based on the received legacy preamble. Then, the fine AGC unit  204  performs fine AGC and frequency offset estimation based on HT preamble. The channel estimation unit  206  performs synchronization and MIMO channel estimation for {tilde over (H)} based on the HT preamble. By using U-D decomposition on the estimated {tilde over (H)} in the U-D unit  208 , the matrices U and D′ in relation (4) above can be computed. By multiplying UH and inverse of D′ (i.e., D′ −1 ) to the received data Y in the units  210  and  212 , respectively, from relation (3) above, one can recover the stream S as:
 D′ −1 U H Y=S  (5) 
         [0026]     Wherein Ŝ . . . Ŝ Nss  are estimates of transmitted data streams.  
         [0027]     The product of power loading and eigenvalue, or the diagonal terms of the matrix D′ in relation (4) above, plays an important role since the operating SNR for each decomposed channel is determined by product of power loading and eigenvalues (i.e., D′). Further, in order for the received HT preambles to have the same SNRS, the reverse water-filling algorithms can be utilized.  
         [0028]     It is noted that replacing the eigen-steering matrix V in  FIG. 1  by the identity matrix, one can obtain an unbeamformed MIMO transmitter and using the same receiver architecture in  FIG. 2  for MIMO detection. Therefore, the transceiver design in  FIGS. 1-2  can be used as a general platform for dual modes (beamforming and unbeamformed MIMO) operations.  
         [0029]     The present invention has been described in considerable detail with reference to certain preferred versions thereof; however, other versions are possible. Therefore, the spirit and scope of the appended claims should not be limited to the description of the preferred versions contained herein.