Abstract:
A flash optical performance monitor for monitoring DWDM channels is disclosed. The monitor is to assess the spectral quality of an optical signal received and to determine from changes in the spectral quality, relative to a known spectral quality indicative of an acceptable signal, an estimate of signal quality. The flash optical performance monitor comprises a spectrometric transducer for performing a spectral decomposition of the optical signal received, and for transforming the decomposed optical signal into electrical-domain data, a memory for storing advanced digital signal processing routines, and a processor in connection with the wavelength optical unit and with the memory. The processor receives the advanced digital signal processing routines and the electrical spectral data, and applies the advanced digital signal processing routines to the electrical spectral data. Also a method for monitoring a quality of data transmission of at least one optical channel is disclosed. The method comprises the steps of capturing a spectrum of an optical signal transmitted on the at least one optical channel at an instance in time, providing a spectrum of a time-domain signal, performing an analysis of the spectrum to determine a quality of the optical signal, and from the quality of the optical signal—a quality of data transmission.

Description:
FIELD OF THE INVENTION  
         [0001]    The present invention relates to the field of optical performance monitoring as currently applied in dense wavelength-division multiplexing.  
         BACKGROUND OF THE INVENTION  
         [0002]    The recent expansion of telecommunications and computer communications, especially in the area of the Internet, has created a dramatic increase in the volume of worldwide data traffic that has placed an increasing demand for communication networks providing increased bandwidth. To meet this demand, fiber-optic networks and dense wavelength-division multiplexing (DWDM) communication systems have been developed to provide high-capacity transmission of multi-carrier signals over a single optical fiber. In accordance with the DWDM technology, a plurality of superimposed concurrent optical signals is transmitted on a single fiber, each signal having a different central wavelength. In DWDM optical networks, optical transmitters and optical receivers are tuned to transmit and receive on a specific wavelength.  
           [0003]    With the widespread deployment of DWDM optical networks, knowing precisely what is happening at the optical layer of the network is quickly becoming a real-time issue for network management. Stable and protected DWDM links cannot be realized without real-time optical monitoring at each channel. For example, as the number of channels deployed in a DWDM optical network increases, say from 40 to 80 or 160, wavelength drifts and power variations are more likely to cause data errors or transmission failures. It is therefore becoming important for network management to dynamically monitor the performance of the communication channels in order to supply the corresponding decision-support systems with information necessary for fault detection and identification, as well as for undertaking efficient restoration actions. To achieve this goal, a new type of fiber-optic products has been developed, the so-called optical performance monitors (OPM).  
           [0004]    An OPM consists of a spectrometric transducer and a computing means. The spectrometric transducer converts an optical signal into a digital signal representative of the spectrum of the input optical signal. The computing means processes that digital signal in such a way as to provide the final result of measurement, i.e. an estimate of the parameters of the optical signal being monitored in a DWDM system. A fractional portion of optical power, typically 2%, is tapped from the mainstream optical signal running through the optical fibre, using a tap coupler. The purpose of tapping is monitoring the optical signal while keeping the properties of the main traffic unchanged. Since the tapped signal will not be added back to the mainstream signal, there is little effect on the properties of the transmitted data, and the OPM thus provides an almost non-invasive measurement. The weak signal tapped from the mainstream optical signal is then directed to an optical unit, by which the channelized wavelength components are separated. The optical unit therefore performs a spectral decomposition of the optical signal; the results of that decomposition are detected by a detector. The detector converts optical signals into electrical signals. The electrical signals are transmitted to the electronics circuitry for processing and digital output.  
           [0005]    The principle of operation of a spectrometric transducer may refer to various physical phenomena that make possible separation of spectral components of the input optical signal. The following devices are examples of technical means used for this purpose:  
           [0006]    a grating or a linear variable filter that enables separation of spectral components in space;  
           [0007]    a tunable filter that enables separation of spectral components in time;  
           [0008]    an optical heterodyne that enables shifting the spectrum in a wavelength range where its analysis is easier.  
           [0009]    A conventional optical network performance monitor typically contains a detection element that is responsive to the combination of all signal channels carried by a main signal stream, and that is operative to generate data containing information of a collective power level provided by all channels. Such data generated in the electrical domain are not sufficient to provide detailed information of channel performance. For instance, if a power level of one of a plurality of channels of the mainstream signal is decreased while a power level of another channel is increased, a total power level measured by such device typically remains constant, thereby providing an inaccurate indication of a monitored network performance. Thus, in order to monitor a condition of an individual channel in a DWDM network, performance monitoring is preferably carried out in the optical layer. An OPM constitutes an integrated spectrometric device at a module level operating in the optical layer, the device which is capable of monitoring the performance of all individual channels, and of providing rapid channel identification, i.e. the estimates of power (P), central wavelength (λ), and optical signal-to-noise ratio (OSNR) for each channel. In order to respond to higher channel counts and transmission speed, the efforts of improving the performance of OPM have been often focused on enhancing the performance of the optical part of the spectrometric transducer which in turn resulted in a high design complexity and high manufacturing risks.  
           [0010]    Following an RHK report (“Vendors Must Adapt Products, Strategies to Stake a Claim in Crowded OPM Market”, Insight, January 2002), OPMs may be classified into three groups: Type-I OPMs, Type-II OPMS, and Type-III OPMs. A Type-I OPM is a monitor capable of providing real-time measurements of power for each DWDM channel. A Type-II OPM is a monitor capable of providing real-time measurements of power, central wavelength, and optical signal-to-noise ratio for each channel. A Type-III OPM is able, moreover, to predict indicators of the service quality provided by a DWDM system such as the bit-error rate (BER) and Q-factor (Q). Currently, those indicators can be correctly measured only with out-of-service test equipment, using a known test sequence in place of the real signal. The determination of BER and Q therefore takes place in the electrical domain, after a signal received by the DWDM receiver is passed on to the electronic circuit. Obviously, this is an expensive, time-consuming and cumbersome method.  
           [0011]    The Type-I OPM commonly uses demultiplexing-type spectrometric transducers. Since a demultiplexing-type component, e.g. an AWG, gives a set of fixed discrete channels with a pre-defined frequency interval, i.e. channel spacing, such OPM is only able to provide power measurements at the wavelength positions corresponding to the DWDM channels. It is obvious that the measurements will be biased when there is thermal drift of some wavelength-related properties of the optical part of the OPM. A type-II OPM is able to provide more network information than a type-I OPM since it not only measures power, but also wavelength variation and OSNR.  
           [0012]    It is not only P, λ, and OSNR of each channel that is of interest of in-service monitoring of a DWDM system, but also the bit error rate, BER, and Q, an indicator of overall quality of the signal. The conventional approach in determining BER makes use of out-of-service test equipment, and is time consuming and expensive. An obvious approach to in-service BER or Q reporting is an electrical-domain approach. It consists of tapping off a part of an optical signal, demultiplexing it through a tunable filter, detecting and then electrically regenerating it through a DWDM-type receiver. However, this approach presents various drawbacks. It is an expensive and time-consuming method since it operates in a serial manner—channel by channel—using serial channel scanning and BER or Q processing. Further, BER or Q is influenced by the receiver noise. Also, the tunable filter introduces signal distortions contributing to an increase in BER (decrease in Q) or a reduction in reliability.  
           [0013]    Typically, in conventional applications, BER is determined by counting bits, a process which takes place in the time domain. Assuming a regular BER value in the order of 10 −12 , and assuming a transmission bit rate of 2.5 Gb/s, it is to be expected that—on average—every 400 s of data flow one faulty bit is to be detected. To determine BER estimate with an acceptable accuracy, a testing time of several hours is necessary.  
           [0014]    It would be highly advantageous to have at one&#39;s disposal alternative, and simpler monitoring methods for faster fault detection and localization. Optical-domain methods, even if less accurate than electrical ones, can provide a fast, a simple, and an economical approach to reach this goal.  
           [0015]    It would be of further advantage to have at hand a system that allows for real-time estimation of OSNR and BER or Q from the data representative of a real-world signal without the need for specific test signal sequences.  
         OBJECT OF THE INVENTION  
         [0016]    It is an object of this invention to provide a transducer and a method for processing signals in which the above-mentioned disadvantages are obviated or mitigated.  
         SUMMARY OF THE INVENTION  
         [0017]    In accordance with an aspect of the instant invention, there is provided a method for monitoring a quality of data transmission of at least one optical channel. The method comprises the steps of acquiring the data representative of the spectrum of a DWDM optical signal transmitted on the at least one optical channel at an instance in time, and performing an analysis of those data to determine some indicators of the quality of that signal and of the quality of data transmission.  
           [0018]    In accordance with another aspect of the instant invention, there is provided a method for monitoring a quality of data transmission of at least one optical channel. The method comprises the steps of providing data representative of a plurality of spectra to a processor for assessing a correlation between said spectra and some indicators of the quality of the DWDM signal and/or of the quality of DWDM data transmission, determining from said correlation a quality of data transmission of the at least one optical channel.  
           [0019]    In accordance with yet another aspect of the instant invention, there is provided a method for estimating BER or Q characterizing the quality of data transmission on at least one optical channel. The method comprising the steps of acquiring the data representative of some time-domain parameters of an DWDM optical signal transmitted on at least one optical channel at an instance in time together with the data representative of the spectrum of said signal, performing an analysis of the acquired data to estimate the value of BER or Q characterizing the quality of data transmission, wherein that estimation of BER or Q is absent counting of bit errors over a period of time sufficient to provide a statistically valid estimate of BER or Q.  
           [0020]    In accordance with an aspect of the instant invention, there is also provided a Flash Optical Performance Monitor (Flash OPM) for monitoring the quality of a DWDM optical signal received. The Flash OPM comprises a spectrometric transducer and a computing means. The latter receives the raw data from the spectrometric transducer, and performs advanced digital signal processing of those data in order to obtain estimates of the DWDM optical signal parameters to be monitored, such as central wavelength, power and OSNR.  
           [0021]    In accordance with an aspect of the instant invention, there is also provided an advanced version of the Flash Optical Performance Monitor (Flash OPM) for monitoring the quality of transmission in the DWDM optical systems using BER or Q as an indicator of this quality. The Flash OPM comprises a spectrometric transducer, an opto-electronic circuit providing data representative of some time-domain parameters of the optical signal, and a computing means. The latter receives the raw data from the spectrometric transducer and from the said circuit, and performs advanced digital signal processing of those data in order to obtain estimates of the DWDM optical signal parameters such as central wavelength, power, OSNR and BER or Q.  
           [0022]    An embodiment of the present invention provides an approach to estimate BER and Q in the optical domain, as they would be recorded at the output of an ideal receiver connected to a monitored point of a network. It overcomes the above-listed drawbacks and provides a fast, simple and economical measurement technique for performance assessment in comparison to the electrical-domain classic approaches. It is applicable to in-service and out-of service approaches.  
           [0023]    Embodiments of the present invention will now be described by way of example only with reference to the accompanying drawings, in which: 
       
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS  
       [0024]    [0024]FIG. 1 is a schematic diagram of an embodiment of an OPM.  
         [0025]    [0025]FIG. 2 is a plot of the representation of two signals provided by an auxiliary transceiver included in the OPM of FIG. 1.  
         [0026]    [0026]FIG. 3 is a schematic diagram of the auxiliary transducer included in the OPM of FIG. 1.  
         [0027]    [0027]FIG. 4 is a flow diagram illustrating the operation of the Flash of FIG. 1.  
         [0028]    [0028]FIG. 5 is a schematic diagram illustrating the methodology of quasi-dynamic measurand reconstruction.  
         [0029]    [0029]FIG. 6 is a schematic diagram illustrating the methodology of quasi-dynamic system calibration.  
         [0030]    [0030]FIG. 7 is a flow diagram illustrating the functionality of a neural network to be used for the determination of BER and/or Q.  
         [0031]    [0031]FIG. 8 shows a schematic diagram of another embodiment of the FLASH of FIG. 1. 
     
    
     DETAILED DESCRIPTION OF THE INVENTION  
       [0032]    The instant invention will now be described with reference to specific embodiments thereof. Of course, the invention is not restricted to a specific hardware device, but is to be utilized in connection with various hardware solutions. Various modifications to the disclosed embodiments will be readily apparent to those skilled in the art, and the general principles defined herein may be applied to other embodiments and applications without departing from the spirit and the scope of the invention. Thus, the instant invention is not intended to be limited to the embodiments disclosed, but is to be accorded the widest scope consistent with the principles and features disclosed herein.  
         [0033]    Referring now to FIG. 1, a schematic representation of an embodiment of a Flash OPM is shown. The Flash OPM  100  includes an optical user interface  10  that receives an optical input signal  12 , and directs the received signal  12  to a spectrometric transducer  14 . The spectrometric transducer  14  separates the input signal  12  into its spectral components and converts those components into corresponding electrical signals. The resultant data set {{tilde over (y)} n }  15  is representative of the spectrum of the optical signal  12 . The spectrometric transducer  14  may utilise an optical element, such as a grating or a variable linear filters to provide a spatial separation of the components of the signal  12  and direct them to a sensor array where they are converted into corresponding electrical signals. Such transducers are well known in the optical art and need not be described in further detail.  
         [0034]    The data set {({tilde over (y)} n }  15  is directed to a processing function  16  that implements one or more of a first set of DSP algorithms (DSP Algorithms I) for signal reconstruction and enhancement. The processor  16  may be a general purpose computer implementing algorithms contained as software instructions resident in a memory device such as a data carrier. Alternatively, the processor may be a dedicated device configured to process the data set in accordance with the selected algorithm. The DSP Algorithms I, executed by the processor  16 , will typically be chosen to perform reconstruction of spectrum parameters, using a non-linear and non-stationary approach, and provides estimates  17  for P, λ, and OSNR. Optionally, the processor  16  may also implement procedures that compensate for variations in temperature, wavelength drifts, aging of the optical components, and the like to enhance the information provided by the processor.  
         [0035]    The output from the processor  16  provides estimates  17  of the power P, wavelength λ and signal to noise ratio OSNR which are sent to an electrical user interface  18 . These outputs based on the spectral analysis quality of the data signal by using one or more of the parameters. For example the channel power may be used as an indicator of quality, or the central wavelength of the channel or by the OSNR.  
         [0036]    BER or Q depends on all the elements of a telecommunication link. The spectrum of the transmitted signal contains more information on BER or Q than the estimates  17  of P, λ, OSNR that are possibly determined on the basis of the data {{tilde over (y)} n }  15  representative of said spectrum, but—as a rule—it does not contain sufficient information on chromatic dispersion and polarization-related effects such as PMD. In order to provide a meaningful estimate of BER or Q, it is necessary to complement spectral information with some time-domain parameters {p k,m } of the optical signal  12 , sensitive to those phenomena. They may be next processed using a number of algorithmic solutions, based both on statistical means of inference and on various methods of multidimensional approximation, including artificial neural networks. To this end, the received signal  12  is also directed to an auxiliary transducer  20  in parallel to the spectrometric transducer  14 . The auxiliary transducer  20  processes the received signal  12  to obtain a data set {{circumflex over (p)} k,m }  27  that represents time-domain parameters {p k,m } of the signal  12 .  
         [0037]    For example, the time domain parameters of a signal s k (t) transmitted by the k th  channel, may be defined as:  
               p     k   ,   m       =     c   ·       ∫     t   start       t   stop              [         s   k          (   t   )       -     s   m   th       ]                ·        t                   Equation                 1                               
 
         [0038]    where t is time, c is a normalization constant, and 
           s   m   th ε[inf{ s   k ( t )| t ε(−∞, +∞) and  k= 1, . . . ,  K }, sup{ s   k ( t )| t ε(−∞, +∞) and  k= 1, . . . ,  K}]   
         [0039]    is the m th  threshold value m=1, . . . M; t start  and t stop  are appropriately chosen limits of integration interval. It will be appreciated that many alternative sets of parameters, that carry the same information about signal distortion, may be defined and the auxiliary transducer  20  constructed accordingly to produce the data set {{circumflex over (p)} k,m }  27 . FIGS. 2 a  and  2   b  show how the signal distortion is reflected in the parameters {{circumflex over (p)} k,m } defined in the above described way. More specifically, in FIG. 2 a  there are shown two demodulated signals  201  and  202 , signal  201  being an undistorted square pulse signal while signal  202  is the same signal after distortion. FIG. 2 b  shows the dependence of the time-domain parameters {{circumflex over (p)} k,m } on the threshold value s m   th  for the undistorted and distorted signals  201  and  202 , respectively. For instance, using Equation 1 with a threshold value of 0.2, the time-domain parameter {{circumflex over (p)} k,m } of distorted signal  202  may be viewed, as shown on FIG. 2 a , as the area  204  under curve (signal)  202  which is above line  203  (threshold). The distorted signal  202  results in time-domain parameters {{circumflex over (p)} k,m } that vary in a non-linear fashion as a consequence of the presence of distortion, which may be seen in FIG. 2 b  by the difference between the tine-domain parameters for the undistorted signal  201  and the distorted signal  202  for a given threshold value s m   th . For example, it may be observed that for the threshold values 0.2, 0.4 and 0.7, the differences  211 ,  214  and  217  between the time-domain parameters  212 ,  215  and  218  of the undistorted signal  201  and the time-domain parameters  213 ,  216  and  219  of the distorted signal  202 , respectively, are not equal. The non linearities may be used to provide an indication of the nature and degree of distortion to which the signal has been subjected. As such, signal  202  is processed so as to identify non-linearities relative to an ideal signal  201 , and from these non-linearities provide an assessment of the degree or type of the distortion. Thus, the time-domain parameters {{circumflex over (p)} k,m } form a function that recognizes the shape of the distorted signal  202  and is indicative of the distortion, which may not be as readily apparent from the spectrum data set {{tilde over (y)} n }.  
         [0040]    In using the parameters defined above, the estimates {{circumflex over (p)} k,m }  27  may be obtained by an auxiliary transducer  20 , shown in FIG. 3, composed of a tunable filter  22  followed by a high-speed photodiode  24 . The output of the diode  24  is processed by an integration circuit  26  to provide the output {{circumflex over (p)}k,m}  27 . The tunable filter  22  is used to select a channel so that the associated photodiode  24  reproduces s k (t) by demodulation, and the integration circuit performs the operation such as that defined by Equation 1 for each of the selected thresholds.  
         [0041]    The output  27  and  15  of the auxiliary transducer  20  and the spectrometric transducer  14 , respectively, are provided to a processor  30  that implements selected ones of a second set of DSP algorithms (DSP Algorithms II) to extract further information from the received signal  12 . The processor  30  may be a specific hardware implementation structured to perform a specific selected algorithm or may be a general-purpose computing device that operates upon the data sets  15  and  27  in accordance with programmed instructions contained on a memory device. The processor  30  executes one or more of the second set of selected DSP algorithms (DSP Algorithms II) to analyse the data {{tilde over (y)} n }  15  and {{circumflex over (p)} k,m }  27 , and provide an estimate  35  for BER or Q. The estimate  35  is next transferred to the electrical user interface  18 . The electrical user interface  18  transfers the estimates  17  and  35  of P, λ, OSNR, and BER or Q to the user that is assessing the performance of a particular channel, and to monitor the quality of a signal transmitted on said channel.  
         [0042]    The interface  18  may function to provide readouts of the parameters being monitored but preferably operates to provide a visual indication of the departure of the parameters from predetermined acceptable levels. Thus the interface may monitor over a period of time the quality factor Q of the respective channels for a period of time and provide a signal indicating if the quality on one or more channels has varied from an acceptable value to an unacceptable value. Similarly, each channel may be monitored for BER and an indication provided if the BER has varied from an acceptable to an unacceptable value. By implementing the monitoring with the auxiliary transducer and processor, it is anticipated that the changes value may detected within one second.  
         [0043]    The processing of the received signal  12  is depicted in the flow diagram of FIG. 4. In a first step  41 , the data {{tilde over (y)} n |n=1, . . . , N} representative of the spectrum of a total DWDM signal are acquired, as well as the estimates {{circumflex over (p)} k,m |k=1, . . . , K; m=1, . . . , M} of some time-domain parameters {p k,m |k=1, . . . , K; m=1, . . . , M} of that signal, that are provided by the auxiliary transducer  20  and carry auxiliary information about signal distortion. The first set of DSP algorithms (DSP Algorithms I), which will be described further below, is used to determine the estimates  17  of the parameters P, λ, and OSNR for each channel—on the basis of the data {{tilde over (y)} n }  15 , step  42 . In step  43 , those data {{tilde over (y)} n }  15  are used again, this time together with the estimates {{circumflex over (p)} k,m )  27  of the time-domain parameters, to determine the estimate  35  of BER or Q. In this step, the second set of algorithms (DSP Algorithms II), which will be described further below, is used. In a last step  44 , there are reported the estimates  17  and  35  of p, λ, OSNR and BER or Q, useful for a network monitoring system.  
         [0044]    The method, as illustrated in FIG. 4, provides a number of advantages compared to traditional out-of-service BER-test techniques. The method is an optical-layer testing method, which is also an in-service method. A BER test of all channels is performed in parallel and thus simultaneously. The method provides a low-cost solution as well as a fast solution to the problem of in-service monitoring of DWDM networks. Test times, according to the method described in FIG. 4, remain substantially constant as channel counts increase. Also, the described method does not depend on the transmission protocol, on the data format or on the generation of complex test signals.  
         [0045]    The first subset of algorithms (DSP Algorithms I), used for determination of the estimates  17  of the parameters P, λ, and OSNR, contains the algorithms for spectrum reconstruction and estimation of spectrum parameters that are well known in the art, for example those described in detail in U.S. Pat. No. 5,991,023 to Morawski et al., issued Nov. 23, 1999, and in U.S. Pat. No. 6,002,479 to Barwicz et al., issued Dec. 14, 1999. These may be, in particular, the algorithms of spectrum reconstruction based on the parameterization of the spectrum of the form:  
         x        (   λ   )       =       ∑     k   =   1     K          [         a     1   ,   k            v        (     λ   -     l   k       )         +       a     2   ,   k              v   Π          (     λ   -     l   k       )           ]                             
 
         [0046]    where:  
         [0047]    a 1 =[α 1,1  . . . a 1,k ] T , a 2 =[α 2,1  . . . α 2,K ] T , I=[l 1  . . . l K ] T  are the vectors of parameters to be estimated;  
         [0048]    I=[l 1  . . . l k ] T  is the vector of ITU-recommended channel wavelength values;  
         [0049]    ν(λ) is a function modelling the normalized spectrum of a monitored telecommunication channel;  
         [0050]    ν π (λ) is a function modelling a normalized pedestal, accompanying the spectrum of a monitored telecommunication channel, in the simplest case:  
           v   Π          (   λ   )       =         1     Δ                   λ   Π              [       1        (     λ   -       Δ                   λ   Π       2       )       -     1        (     λ   +       Δ                   λ   Π       2       )         ]       .                           
 
         [0051]    In this case, the estimates  17  of the channel parameters P, λ, OSNR may be calculated directly from the estimates of a 1 , a 2 , and 1.  
         [0052]    The second set of DSP algorithms (DSP Algorithms II), used for extracting useful BER and Q information, may be constructed according to the following principles. A spectrometric transducer  14  converts input optical signal into a set of data {{tilde over (y)} n }  15  representative of the spectrum of this signal. The spectrometric transducer  14  is, for example, part of a Type-II FLASH device, but it is not restricted to such devices and applications. An output-related discretisation of a wavelength axis is defined by a sequence {λ n } such that λ min =λ 1 &lt;λ 2 &lt;. . . &lt;λ N−1 &lt;λ N =λ max  where N is a number of data. For example, in a Type-II Flash OPM having a detector array, such as the one described in FIG. 1, N represents a number of photodiodes in the detector array. Thus, the average interval between wavelengths, in the given example equivalent to the distance two neighbouring photodiodes are adjusted to each other, is given by Δλ=(λ max −λ min )/(N−1). It is assumed that the data {{tilde over (y)} n }  15  represent a spectrum of K channels combined in a DWDM system under consideration. A subsequence of data {{tilde over (y)} n |n=N k,min , . . . N k,max } is used, together with the information indicative of the signal distortion within the time-domain parameters {{circumflex over (p)} k,m }  27  provided by the auxiliary transducer  20 , for estimation of BER or Q. Further, the length of this subsequence is variable, and amounts for example to 3, 4, 5, 6 or more elements. In the following, for the sake of simplicity, considerations are limited to one channel only, and the symbol {{tilde over (y)} n } is used for denoting this subsequence. A person of skill in the art is able to extend the concept with ease to any other number of channels.  
         [0053]    The problem of determining BER or Q may be solved in a broad context of algorithmic options, which are derived from ideas of quasi-dynamic measurand reconstruction that is a well-established and well-recognised methodology in digital signal processing, as for example illustrated in the paper “The Role of Digital Signal Processing in Measurement Science” published in “ Measurement Science—A Discussion ” (Ohmsha Press Pub., Tokyo 2000, pp. 77-102). High redundancy of measurement information in raw measurement data is the main distinctive feature of any problem of quasi-dynamic measurand reconstruction. Consequently, implicit or explicit compression of data is present in any procedure for solving such a problem. The value of a scalar measurand x, BER or Q, is estimated on the basis of a subsequence of data {{tilde over (y)} n }  15  representative of the channel spectrum and the parameters {{circumflex over (p)} k,m }  27  to which the measurand is approximately related.  
         [0054]    A large family of DSP methods for estimation of BER or Q may be derived from the general methodology for solving problems of quasi-dynamic measurand reconstruction. This methodology consists of two steps: compression of the data {{tilde over (y)} n }  15  and {{circumflex over (p)} k,m }  27 , i.e. transformation of the data {{tilde over (y)} n }  15  and {{circumflex over (p)} k,m }  27  into an estimate {circumflex over (p)}  32  of a vector of informative parameters p, {{tilde over (y)} n }, {{circumflex over (p)} k     m   }→{circumflex over (p)}, and subsequent estimation of x on the basis of {circumflex over (p)}, {circumflex over (p)}→{circumflex over (x)}. This methodology is illustrated in the schematic diagram shown in FIG. 5. Inputs containing the subsequence {{tilde over (y)} n }  15  and {{circumflex over (p)} k,m }  27  are provided to a data compressor  31 . The data compressor  31  compresses the subsequence {{tilde over (y)} n }  15  and {{circumflex over (p)} k,m }  27  to obtain a set containing an estimate {circumflex over (p)}  32 , which is provided to a BER or Q estimator  33 . When properly calibrated, the BER or Q estimator  33  responds with an output set  35  containing an estimate  35  {circumflex over (x)} of x, i.e. of BER or Q. A complexity of the method illustrated in FIG. 5 depends on a number of informative parameters, i.e. the dimension of the vector {circumflex over (p)}  32 . The greater the number of informative parameters, the more time is required both for calibration and for BER or Q estimation.  
         [0055]    The calibration of the Flash OPM  100  is an important step in the methodology described above. It is to be performed on the basis of reference data, which are structured as {tilde over (D)} cal ={{tilde over (x)} v   cal , {{tilde over (y)} n,v   cal }&amp;{{circumflex over (p)} m,v   cal }|v=1, . . . , N cal }. In FIG. 6, a schematic diagram for a method of calibration is outlined. An input containing the subsequence {{tilde over (y)} n,v   cal }  61  and {{circumflex over (p)} m,v   cal }  62  is provided to a data compressor  63 . The data compressor  63  compresses the subsequence {{tilde over (y)} n,v   cal }  61 , and computes an estimate of a vector of informative parameters {circumflex over (p)} v   cal    64 , corresponding to reference values {tilde over (x)} n,v   cal , on the basis of {{tilde over (y)} n,v   cal } and {{circumflex over (p)} m,v   cal } for v=1, . . . , N cal . The set  64  containing the parameters {circumflex over (p)} v   cal  is provided to a BER or Q estimator  65 . The BER or Q estimator  65  responds with an output set  66  containing a datum {circumflex over (x)} n,v   cal    66 . In a data adjustor  67 , the data {circumflex over (x)} n,v   cal    66  and {tilde over (x)} n,v   cal  are compared. The result of this comparison is provided as feedback to the data compressor  62  and the BER or Q estimator  65 , where in turn this information is utilized in constructing an approximation of the relationship p→x using a set of input-output pairs: {{circumflex over (p)} v   cal ,{tilde over (x)} v   cal |v=1, . . . , N cal }.  
         [0056]    A large variety of algorithms is possibly generated by combining various techniques of data compression with various types of approximators. For example, the following techniques of data compression are optionally used: principal component analysis, computation of inner products of the data {{tilde over (y)} n }  15  and {{circumflex over (p)} k,m }  27  and linearly independent sequences {e j,n |j=1, . . . , J}, approximation of the spectrum y(λ) on the basis of {{tilde over (y)} n }  15  and {{circumflex over (p)} k,m }  27  using a parameterised function ŷ(λ n ;a) with a being a vector of parameters, and computation of the moments of the spectrum y(λ) on the basis of {{tilde over (y)} n }  15 . In the considered case, an application-specific vector of informative parameters could contain estimates  17  of P, λ, and OSNR, the estimates determined on the basis of ({tilde over (y)} n }  15  and {{circumflex over (p)} k,m }  27 . The most evident candidate for the measurand estimator, i.e. the BER or Q estimator, is a neural network being a universal approximator. Alternatively, B-splines are to be considered as measurand estimators. A person of skill in art will be able to suggest further methods of data compression and final measurand estimation.  
         [0057]    For example, following a straightforward approach, a Radial Basis Functions (RBF) neural network  34  is designed as illustrated in the schematic diagram shown in FIG. 7. This particular network performs both the function of data compressor and of BER/Q estimator. The neural network  34  receives as inputs data sets {{tilde over (y)} n }  15  and {{circumflex over (p)} k,m }  27 . The neural network  34  is trained to respond with an estimate {circumflex over (x)}  35  of x (BER or Q) on the basis of {{tilde over (y)} n } and {{circumflex over (p)} k,m }. It is important for training the network that the data set {{tilde over (y)} n }  15  stem from a low-resolution spectrometric transducer and the parameters {{circumflex over (p)} k,m }  27  from an auxiliary transducer. The sets of data used for training preferably represent a telecommunication signal distorted in various ways by its propagation through optical elements such as fibers, amplifiers, and filters. Instead of a RBF neural network, any other universal approximator may be used, e.g. another type of neural network or a multi-dimensional spline function. Instead of one neural network a cascade of two neural networks may be designed: the first to perform the function of data compressor, the second—of BER/Q estimator.  
         [0058]    Referring now to FIG. 8, a schematic representation of another embodiment of the Flash OPM  100   a  is shown, in which the Flash OPM  100   a  is adapted so as to provide data suitable for use in a special application related to performance monitoring, viz. controlling a Digital Gain Equalizer (DGE). Like components will be described with like reference numerals with a suffix “a” added for clarity. The Flash OPM  100   a  includes an optical user interface  10   a,  that provides received signal  12   a  to a spectrometric transducer  14   a.  A processor  16   a  implements a first set of DSP algorithms (DSP Algorithms I). The output of the processor  16   a  is applied to the electrical user interface  18   a  and to a further processor  50  that implements a further set of DSP algorithms (DSP Algorithms III). The received signal  12   a  is also fed to an auxiliary transducer  20   a  and to the processor  30   a  for implementing the second set of DSP algorithms (DSP Algorithms II) as described above to obtain estimate  35   a  of BER or Q. The processor  50  utilises the DSP algorithms (DSP Algorithms II) to process the estimates  17   a  of P, λ, and OSNR according to information suitable for control of DGE. A person of skill in the art easily envisions further applications of DSP-type processing units. These applications are feasible, since the spectrum retrieved by the spectrometric transducer, such as  14 ,  14   a ,  and processed by the processors  16 ,  16   a,  inherently contain relevant and significant information characterizing the input optical signal.  
         [0059]    The data processing performed by optical performance monitors, such as  100  and  100   a  takes place within a time range of 50-200 milliseconds. This allows for in situ monitoring of an optical signal transmitted on a given channel, and for immediate undertaking of measures to reroute an optical signal to an alternative channel, once a too high value of BER or too low value of Q is detected. Assuming a response time of the monitor of 50 milliseconds, and a transmission bit rate of 2.5 Gb/s, a data buffer of 1.6 MB is sufficient to ensure that no data are lost during the detection of a fault-signal ling BER or Q value and rerouting of an optical signal. By shifting the determination of BER or Q values from the electrical domain into the optical domain, a continuous, real-time quality assessment of an optical channel is possible, and it is further possible to route data transmission without a significant loss of information.  
         [0060]    Although the present invention has been described with respect to specific embodiments thereof, various changes and modifications are optionally carried out by those skilled in the art without departing from the scope of the invention. Therefore, it is intended that the present invention encompass such changes and modifications as fall within the scope of the appended claims.