Abstract:
A set of CMOS-based amplifiers amplify signals from a set of photosensors within a large photosensitive imaging device. When the imaging device reads out image signals, each amplifier is selected for operation only within a brief time window when the particular photosensor associated therewith is reading out. Incidental to reading out a signal through a particular amplifier, all nodes which are capacitively coupled to the input node of the amplifier are biased to a known magnitude. In this way, residual charges remaining in the amplifier from a previous readout will not distort subsequent signals read through the amplifier.

Description:
CROSS REFERENCE TO RELATED APPLICATION 
     Cross-reference is made to the following U.S. Pat. No. 6,552,324, for “Selectable Pixel Amplifier for Use in a Photosensor Array”, assigned to the Assignee hereof. 
    
    
     FIELD OF THE INVENTION 
     The present invention relates to an image sensor array, such as found, for example, in digital scanners, copiers, and facsimile machines. More particularly, the present invention relates to a selectable amplifier which can be associated with at least one individual photosensor in such a sensor array. 
     BACKGROUND OF THE INVENTION 
     Image sensor arrays typically comprise a linear array of photosensors which scan an image-bearing document and convert the small image areas viewed by each photosensor to image signal charges. Following an integration time, the image signal charges are amplified and transferred to a common output line or bus through successively actuated multiplexing transistors. 
     In the scanning process, bias and reset charges are applied to each photosensor (such as a photodiode) in a predetermined time sequence during each scan cycle. In a particular embodiment of such an image sensor array, a two-stage transfer circuit is provided for transferring the image signal charges from the photodiodes. A bias charge is applied to each photodiode through a bias charge injection transistor coupled to a node between the photodiode and the input to the transfer circuit. From the transfer circuit, the image-based charges are caused to pass through an amplifier circuit, one amplifier circuit being typically provided for each photodiode, or at least to each RGB-color triplet of color-sensitive photodiodes. 
     In an active photosensor array it is typical to have individual photosensors transfer image-related charges therefrom onto capacitors, one capacitor being associated with each photosensor. This “reset capacitor” temporarily stores the image-related charge, which is subsequently transferred through an amplifier associated with the reset capacitor. Then the amplified voltage signal resulting from the transfer is read out as a video signal on a video line. 
     The present invention is generally directed to the design of an amplifier which can be associated with an individual reset capacitor which in turn is associated with a particular photosensor in an image sensor array. As is known in the prior art, particularly in the &#39;423 patent referenced below, a preferred design for an image sensor array having an amplifier associated on a one-to-one basis with a set of photosensors is to have each amplifier be “selectable” so that the amplifier is fully operational only during the short period of time when the particular amplifier is transferring a charge from a reset capacitor onto the video line: for the bulk of the time of operation, when the particular reset capacitor is not transferring a signal onto the video line, the amplifier is “deselected,” or another words put in a low-power-consumption mode, thus saving power consumption of the entire array. 
     A practical problem which occurs when using selectable amplifiers in the image sensor array is that, when an amplifier associated with a particular reset capacitor and photosensor is deselected following a signal transfer, a residual charge remains within the amplifier circuitry, and this residual charge will capacitively couple unpredictable amounts of charge onto the reset node capacitance for the next time an image-related charge is transferred from the capacitor onto the video line. This unpredictable additional amount of charge thus placed on the reset capacitor will distort the signal charge of the subsequent image reading. 
     It is an object of the present invention to provide circuitry for a selectable pixel amplifier which will reset to a known voltage following every readout from a reset capacitor onto a video line. 
     DESCRIPTION OF THE PRIOR ART 
     Bazes, “Two Novel Fully Complementary Self-Biased CMOS Differential Amplifiers,”  IEEE Journal of Solid - State Circuits,  Vol. 26, No. 2, February 1991, pp. 165-168, discloses designs of differential amplifiers having fully complementary configurations and which are self-biased through negative feedback. U.S. Pat. Nos. 4,857,476 and 4,958,133 by the same author show related amplifier designs. 
     U.S. Pat. No. 5,493,423 discloses an amplifier circuit which can be associated with an individual photosensor in an image sensor array. With each cycle of passing an image signal through an amplifier, a low standby current is applied to certain transistors within the amplifier until the next signal is to be output. Critical nodes within the amplifier are caused to settle to known charge values before each image signal is passed therethrough. 
     SUMMARY OF THE INVENTION 
     According to one aspect of the present invention, there is provided an image sensor array, comprising a plurality of photosensors, with a transfer circuit associated with each photosensor. Selection means cause each transfer circuit to output an image-related charge to an output line. An amplifier is interposed between each transfer circuit and the output line, the amplifier including an input node connected to the reset capacitor, and an input stage connected to the input node. The input stage includes a plurality of transistors, the transistors in the input stage forming a set of input stage nodes capacitively coupled to the input node. Reset means cause all of the input stage nodes in the amplifier to be biased to at least one known magnitude incidental to the amplifier transferring a charge from the transfer circuit to the output line. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is a schematic view of an image scanning array having an array of photosensor cells, each cell having a photodiode with two-stage transfer circuit and amplifier for transferring image signal charges from the photodiodes to a common output bus; 
     FIG. 2 is a schematic diagram of a selectable amplifier circuit, as could be used in the sensor array of FIG. 1, according to the present invention; and 
     FIG. 3 is a schematic diagram of an amplifier circuit according to another embodiment of the present invention. 
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     FIG. 1 shows an image sensor array with two stage transfer, designated generally by the numeral  10 , of the type to which the present invention is directed. Image sensor array  10  includes a chip  12  of silicon with a plurality of photosites in the form of photodiodes  14  thereon. Photodiodes  14  are in closely spaced juxtaposition with one another on chip  12  in a linear array or row  16 . Several smaller arrays such as array  10  can be abutted together end to end with one another to form a longer array, i.e., a full width or contact array, with spacing between the photodiodes inside the chip thereby maintaining photodiode pitch across the entire full width of the composite array. 
     While photodiodes  14  are shown and described herein, other photosite types such as amorphous silicon or transparent electrode MOS type photosites may be envisioned. Further, while a one dimensional sensor array having a single row  16  of photodiodes  14  is shown and described herein, a two dimensional sensor array with plural rows of photodiodes may be contemplated. 
     Each photodiode  14  has a two stage transfer circuit  20  associated therewith which together with the photodiode and an amplifier  33  form a photosite cell  15  at the array front end. In each cell  15 , the image signal charge from the photodiode  14  is amplified to bring the image signal charge to a desired potential level prior to transferring the charge to a common video output line or bus  22 . Suitable shift register and logic circuitry  24  provides timing control signals ΦPIX (with an optional complement, ΦNPIX) for connecting each pixel cell  15  to bus  22  in the proper timed sequence; a shift register such as  24  typically includes a set of stages therein, each stage in this embodiment being associated with one photosite cell  15 , and thus associated with one amplifier, as can be seen as the set of ΦPIX and ΦNPIX lines emerging from shift register  24 . 
     Image sensor array  10  may for example be used to raster scan a hard-copy document, and in that application, the document and sensor array  10  are moved or stepped relative to one another in a direction (i.e., the slow scan direction) that is normally perpendicular to the linear axis of array  10 . At the same time, the array scans the document original line by line in the direction (i.e., the fast scan direction) parallel to the linear axis of the tray. The image line being scanned is illuminated and focused onto the photodiodes  14 . During an integration period, a charge is developed on each photodiode proportional to the reflectance of the image area viewed by each photodiode. The image signal charges are thereafter transferred by two stage transfer circuits  20  via amplifier  33  to output bus  22  in a predetermined step by step timed sequence. 
     Preferred designs for the transfer circuits  20  can be found in U.S. Pat. Nos. 4,737,854; 5,081,536; or U.S. Pat. No. 5,105,277. In each of these references the transfer circuit  20  is of the “two-stage transfer” type, although it is conceivable to use the amplifier of the present invention with, for instance, a single-stage transfer circuit associated with each photodiode. 
     FIG. 2 is a schematic view of a design of amplifier which could be used as amplifier  33  in the context of the image sensor array of FIG.  1 . The amplifier shown in FIG. 2 is conceptually similar to the “very-wide-common-mode-range differential amplifier,” or VCDA, described in the article by Bazes referenced above. Both the FIG. 2 amplifier and the Bazes design represent a CMOS differential amplifier with wide input dynamic range, which is fully complementary and entirely self-biased. The design shown in FIG. 2 is particularly useful for providing a desirably linear unity-gain amplification from zero to VDD (in terms common in the art of CMOS circuitry, this is known as the “voltage of the drain,” or full power supply range). 
     In overview, the basic amplifier of FIG. 2 functions as follows. The amplifier, generally indicated as  33 , accepts an image-based voltage signal V input  from the reset capacitor in the associated transfer circuit  20  and ultimately outputs a voltage signal V output  to the video output line. There is provided, at V input  a differential pair of p-devices M 1 A and M 1 B. The differential pair of p-devices M 1 A and M 1 B are combined as shown with a differential pair of n-devices, M 2 A and M 2 B. The p-devices M 1 A and M 1 B share a common current source, VDD actuable through transistor M 3 , while the sources of the n-differential pair M 2 A and M 2 B share a common ground actuable through transistor M 4 . The n-differential pair M 2 A and M 2 B is useful for providing an output V output  in the range of 2-5 volts, while the p-differential pair M 1 A, M 1 B is useful for outputting voltages in the range of 0-3 volts. With reference to the claims below, the set of complementary CMOS transistor pairs M 1 A, M 1 B, M 2 A, and M 2 B forms a folded cascode amplifier in itself and represent the “input stage” for the overall amplifier  33 . 
     Voltage source VDD forms balanced rails providing summing current to the two kinds of differential pairs, while the transistors M 10  and M 11  proximate to voltage source VDD form a push-pull output driver stage. The line connecting V output  to the gate of devices M 1 A and M 2 A forms the feedback loop which causes the amplifier  33  to be a unity-gain amplifier. 
     As the input voltage V input  rises from a low to high voltage, the p-type input devices M 1 A, M 1 B switch from full conduction to no conduction and the n-type devices M 2 A, M 2 B switch from no conduction to full conduction currents. In other words, the n-channel devices are inactive in the region near ground and the p-channel devices are inactive in the region near VDD. Between these extremes, both pairs are active. 
     The bias current to the pairs of devices M 1 A, M 1 B and M 2 A and M 2 B in the input stage is supplied by load devices M 3  and M 4 . The currents through load devices M 3  and M 4  must be identical; any differences in currents through M 3  and M 4  devices would result in extreme shifts in amplifier-bias voltages. Therefore, external biasing of load device M 3  for the p-channel pair and load device M 4  for the n-channel pair is not desirable. The self-biasing scheme is created by connecting both M 3  and M 4  to a single internal bias node, indicated as V bias  in FIG.  2 . The self-biasing of the amplifier creates a negative-feedback loop that stabilizes the bias voltages for M 3  and M 4 . 
     The current paths are formed by M 3 , M 1 A, and M 8 A or M 3 , M 1 B, and M 8 B for the p-devices, and are formed by M 5 A, M 2 A, and M 4  or M 5 B, M 2 B and M 4  for the n-devices. Precise balancing of currents through the two paths is dependent on the ratios of the devices M 6 A to M 7 A (and M 6 B to M 7 B) as well as M 5 A to M 8 A (M 5 B to M 8 B). The cascode stage formed by devices M 5 A, M 6 A, M 7 A, and M 8 A on the biasing side, and the cascode stage formed by devices M 5 B, M 6 B, M 7 B, and M 8 B on the output side are identical and complementary to each other. Each cascode stage forms a summing circuit for the currents through transistors M 1 A and M 2 A (or M 1 B and M 2 B) of the input stage. 
     The cascode stage formed by M 5 B through M 8 B drives the output buffering stage. The output stage is formed by two common-source output transistors M 10  and M 11 . In order to provide a stable operation, capacitors CM 1  and CM 2  are used for frequency compensation. The output is fed back to the inputs of devices M 1 A and M 2 A of the differential amplifier. The input signal is connected to the gates of M 1 B and M 2 B as shown in FIG.  2 . The differential amplifier output is in phase with the input signal. 
     Returning to FIG. 1, it is most desirable, from the standpoint of overall power consumption of the image sensor array  10  that individual amplifiers  33  be powered up for operation only in the narrow window of time during each readout in which the particular photodiode  14  associated with a single amplifier is transferring a signal therethrough. If a typical sensor array  10  on a single chip  12  includes approximately 250 photodiodes  14 , it will be evident that the overall duty cycle of any individual amplifier  33  will be quite short in proportion to the total time of operation of the image sensor array  10 . 
     The FIG. 2 amplifier includes, in addition to the original inputs and outputs V input  and V output , inputs for selecting the amplifier  33  as a whole: as shown in FIG. 2, there are inputs ΦPIX and ΦNPIX which are complements of each other. The inputs ΦPIX and ΦNPIX are readily derived from the standard suitable shift register and logic circuitry  24  such as shown in FIG.  1 . When an input ΦPIX is high, the amplifier  33  is “selected” and operates as an amplifier. Significantly, when ΦPIX is low, and by definition when ΦNPIX is high, the amplifier  33  is powered down. 
     Looking at the different areas in which a high value of ΦNPIX (a “deselect” signal) affects the circuit of FIG. 2, it will first be noted that a high ΦNPIX will disconnect the output from any downstream circuitry, as shown at devices M 12  and M 13 . A high value of ΦNPIX will also create a channel in transistor M 14 , which has the effect of shutting off all the n-devices M 8 A, M 4 , M 8 B. The activation of ΦNPIX at device M 9 B effectively removes any path between the n- and p-devices within the amplifier  33 . An additional VDD input causes the amplifier  33  to match the impedance of a new signal when the amplifier  33  is next selected. 
     With particular regard to the present invention, in addition to the basic circuitry of amplifier  33 , there is provided circuitry to ensure that, following each readout of an image signal by a particular amplifier  33 , the amplifier  33  is reset, at its input node, to a consistent well-defined potential. As mentioned above, one practical problem with individually-selectable amplifiers is that, following the readout of each individual image-related charge from a transfer circuit, the amplifier is left with an unpredictable charge at its input node, and this unpredictable charge at the input node will couple to a subsequent image-related charge caused by the next reading from the photosensor; or, more briefly, a residual charge left on the amplifier will be a source of noise for a subsequent signal read through the amplifier. To address this problem, the present invention includes, in addition to the basic circuitry of an amplifier  33 , means for deliberately resetting the potential on the input node following every transfer of charge from a reset capacitor to the video line through the amplifier. In a preferred embodiment of the present invention, this reset is accomplished by deliberately using the known power voltage VDD to reset all of the complementary CMOS transistor pairs forming the input stage for the amplifier  33 . In the illustrated embodiment of FIG. 2, this input stage is represented by transistor pairs M 1 A, M 1 B, M 2 A, and M 2 B. 
     With particular reference to the FIG. 2 embodiment, it can be seen that there is provided two “input stage reset lines,” indicated as  50  and  52 , which selectably connect (when pixel signal Φ PIX  is low) the voltage VDD to, respectively, the node associated with transistors M 2 B and M 1 B respectively. Also, the other two nodes of the input stage transistors M 1 B and M 2 B are connected, via lines  54  and  56 , to VDD incidental to the power-down structure of the circuitry  33 . What is important within the design of the FIG. 2 embodiment is that when a particular amplifier  33  and a sensor array is deselected, all of the nodes which are capacitively coupled to the floating input V input  are reset to a known value during reset and charge transfer. In this particular embodiment, the known value happens to be VDD for purposes of convenience, but it is conceivable that all the nodes could be deliberately reset to another known value, such as ground or some other fixed number: the design choice of what known value the nodes should be reset to will depend on the particular configuration of the amplifier as a whole. 
     FIG. 3 shows an alternate embodiment of an amplifier according to the present invention, in which once again all of the nodes in the input stage are reset to known values, except in this case certain of the nodes are reset, through line  58  which substitutes for the line  50  in the FIG. 2 embodiment, not to the known VDD but to another predetermined potential ΦSTBY, a standby which may incidentally be available on the chip. (For instance, the circuit in the &#39;423 patent described above includes provision for a relatively low fixed standby voltage available to the various amplifiers when they are not transferring a charge onto the video line.) 
     For the present invention to accomplish its purposes, the important factor is that all of the nodes which are capacitively coupled to the input node of the amplifier are reset to consistent well-defined values (which can generally be any value, as long as it is and predictable) incidental to every use of the amplifier for transferring a charge ultimately from a photodiode to a video line. In the particular embodiments of FIGS. 2 and 3, these nodes are the transistors which form the input stage immediately relevant to the input node of the amplifier  33 . However, it is conceivable, to accomplish the basic function of the present invention with, for example a software scheme, i.e., using a microprocessor-controlled device to artificially insert a predetermined charge or potential on the input node of each amplifier incidental to every use of the amplifier. 
     While the invention has been described in detail with reference to specific and preferred embodiments, it will be appreciated that various modifications and variations will be apparent. All such modifications and embodiments as may occur to one skilled in the art are intended to be within the scope of the appended claims.