Abstract:
Techniques are provided for the implementation of a signal processing circuit which expands the dynamic range of the signal processing circuit without interrupting the output of the circuit. The techniques can receive an input signal, process the signal through one of a plurality of signal processing circuits, and switch to processing the signal through another of the plurality of signal processing circuits without disturbing the output of the system.

Description:
[0001]    The analog floating point technique addresses the problem of distortion in the output whenever the amplification factors change. E. Blumenkrantz, “The analog floating point technique,” Proc. IEEE Symposium on Low Power Electronics, p. 72-73, 1995. This technique avoids distortion by altering the state variables of the signal processor when the amplification factors change. However, implementation of the analog floating point technique is complicated to implement, and is sensitive to parasitics and component mismatch. Accordingly, there is a need for circuits which expand the dynamic range of a signal processor without interrupting the output of the system or causing distortion.  
         SUMMARY OF THE INVENTION  
         [0002]    It is therefore an object of this invention to provide a circuit which has a large dynamic range and which operates in an energy-efficient manner without interrupting the output of the circuit or causing distortion.  
           [0003]    In accordance with the present invention, there is provided a signal processing system having a system input for receiving an input signal having an in-band component and an out-band component, and a system output for providing a system output signal. The system further includes a plurality of signal processing circuits each having an input coupled to the system input and an output for providing a respective output signal, each one of the signal processing circuits being adapted for optimal processing of input signals over a different range of in-band component to out-band component ratios. Also included are a plurality of switches each having a switch input coupled to the output of a respective one of the signal processing circuits, a switch output connected to the system output and a switch control input responsive to a first switch control signal for connecting the switch input to the switch output and responsive to a second switch control signal for disconnecting the switch input from the switch output. Finally, there is provided a signal strength detector having at least one input each coupled to the output of a preselected one of the signal processing circuits and a plurality of outputs each coupled to the switch control input of a respective one of the plurality of switches. The signal strength detector is responsive to a comparison of the strength of the output signal of each one of the signal processing circuits having an output coupled to the at least one input of the signal strength detector with at least one limit for selecting a particular one of the signal processing circuits and for providing a first switch control signal to the switch control input of the switch having its switch input coupled to the output of the particular one of the signal processing circuit. The signal strength detector providing the second switch control signal to the switch control input of each one of the switches having its switch input coupled to the output of a respective one of the signal processing circuits not selected by the signal strength detector.  
           [0004]    According to another embodiment of the invention, there is provided a signal processing system having a system input for receiving an input signal and a system output for providing a system output signal, and a plurality of signal processing circuits each having an input coupled to the system input and an output for providing a respective output signal. Each signal processor having a different saturation level and a different signal-to-noise ratio. Also included are a plurality of switches each having a switch input coupled to the output of a respective one of the signal processing circuits, a switch output coupled to the system output, and a switch control input responsive to a first switch control signal for connecting the switch input to the switch output and responsive to a second switch control signal for disconnecting the switch input from the switch output. Finally there is provided a signal strength detector having an input coupled to the system input and a plurality of outputs each corresponding to a respective one of the signal processing circuits. The signal strength detector is responsive to a comparison of the strength of the input signal received at the system input with at least one limit for selecting a particular one of the signal processing circuits having a respective saturation level and a respective signal-to-noise ratio suitable or processing the input signal and for providing the first switch control signal to the switch control input of a respective one of the plurality of switches having its switch input coupled to the output of the selected one of the signal processing circuits and for providing the second switch control signal to the switch control inputs of respective ones of the switches having the switch input coupled to the output of respective ones of the signal processing circuits not selected by the signal strength detector.  
           [0005]    According to another embodiment of the present invention, there is provided a signal processing system having a system input for receiving an input signal, a system output for providing a system output signal, and a first and second signal processing circuit each having an input, an output, a power control input responsive to a first power control signal for causing the signal processing circuit to be in a powered up state and responsive to a second power control signal for causing the signal processing circuit to be in a powered down state, and at least one bias control input responsive to at least one bias control signal for biasing the signal processing circuit for optimal processing of the signal having a respective signal strength. Also provided are a plurality of output switches each having a switch input connected to the output of a respective one of the first and second signal processing circuits, a switch output coupled to the system output and a switch control input responsive to the first switch control signal for connecting the switch input to the switch output and being responsive to a second switch control signal for disconnecting the switch input from the switch output. At any given time one of the first or second signal processing circuits is active by being in a powered up state, receiving at least one bias control signal at its at least one bias control input and having its output connected to the system output by a respective one of the output switches, and the other one of the first and second signal processing circuits is inactive by being in a powered down state and having its output disconnected from the system output by a respective one of the output switches. Also provided is a signal strength detector having a first and second input connected to respective internal nodes of the first and second signal processing circuits and at least one input for specifying at least one bias control signal, if any, to be applied to the at least one bias control input of the inactive one of the signal processing circuits. The signal strength detector is responsive to a comparison of the strength of a signal on the respective internal node of an inactive one of the signal processing circuits with at least one limit for determining whether at least one bias control signal is to be applied to the at least one bias control input of the inactive one of the signal processing circuits for changing the bias thereto and for providing on the at least one output at least one signal specifying, if any, the at least one bias control signal to be applied to the bias control input an inactive one of the signal processing circuits. There is further provided a bias selector responsive to the at least one output signal provided on the at least one output of the signal strength detector for providing on at least one first output the at least one bias control signal specified by the at least one signal on the at least one output of the signal strength detector to the at least one bias control input of the inactive one of the signal processing circuits and providing on a second output a signal indicating that at least one bias control signal has been applied to the inactive one of the signal processing circuits. Finally there is included a timer circuit responsive to the signal on the second output of the bias selector circuit for providing the first power control signal to the power control input of the inactive one of the signal processing circuits, and after a predetermined delay for applying the first switch control signal to the switch control input of the switch having its input coupled to the output of the inactive one of the signal processing circuits and applying the second switch control signal to the switch control input of the switch having its switch input connected to the output of the active one of the signal processing circuits and applying the second power control signal to the power control input of the active one of the signal processing circuits. According to a further embodiment of the present invention, there is provided a signal processing system having a system input for receiving an input signal having an in-band component and an out-band component, and a system output for providing a system output signal. The system further includes a plurality of signal processing circuits each having an input coupled to the system output, an output for providing a respective output signal and a power control input responsive to a first power control signal for causing the signal processing circuit to be in a powered up state and responsive to a second power control signal for causing the signal processing circuit to be in a powered down state, each one of the plurality of signal processing circuits being adapted to have a different saturation level and signal-to-noise ratio for optimal processing of signals having a different range of in-band component to out-band component ratios. Also provided is a plurality of output switches each one having an input coupled to the output of a respective one of the plurality of signal processing circuits, an output connected to the system output and a switch control input responsive to a first switch control signal for connecting the input of the switch to the output of the switch and responsive to the a second switch control signal for disconnecting the input of the switch from the output of the switch. Also provided are a plurality of output switches each one having an input coupled to the output of a respective one of the plurality of signal processing circuits, an output connected to the system output and a switch control input responsive to a first switch control signal for connecting the input of the switch to the output of the switch and responsive to a second switch control signal for disconnecting the input of the switch from the output of the switch. In addition, the system includes a signal strength detector having a first input connected to the system output, at least one output for providing a signal indicating a selective one of the plurality of signal processing circuits. The signal strength detector is responsive to the comparison of the strength of an output signal with at least one limit for selecting one of the plurality of signal processing circuits for processing the input signal and providing at least one signal on the at least one output indicating the signal processing circuit selected by the signal strength detector. Finally there is included a timer circuit having at least one input each coupled to a respective one of at least one output of the signal strength detector and a first plurality of outputs each one connected to the power control input of the respecdtive one of the plurality of signal processing circuits and a second plurality of outputs each one connected to the switch control input of a respective one of the plurality of output switches. The timer circuit is responsive to at least one signal provided by the signal strength detector for providing the first power control signal to the power control input of the signal processing circuits selected by the signal strength detector and providing after a predetermined delay the first switch control signal to the switch control input of a respective one of the plurality of output switches having its input connected to the output of the signal processing circuits selected by the signal strength detector to thereby connect the output of the signal processing circuit selected by the signal strength detector to the system output and providing after the predetermined delay the second switch control signal to the switch control input of respective ones of the plurality of output switches each having a switch input connected to the output of a respective one of the plurality of signal processing circuits not selected by the signal processing detector to thereby disconnect the output of each one of the signal processing circuits not selected by the signal strength detector from the system output. The timer circuit is responsive to at least one signal provided by the signal strength detector for providing at least the predetermined delay the second power control signal to the power control input of each one of the plurality of signal processing circuits not selected by the signal strength detector. According to another aspect of the present invention, there is provided a method for processing an input signal received by a system input to derive an output signal at a system output. The method includes providiing a plurality of signal processors each having an input coupled to the system output and an output. Each one of the signal processors is adapted to process an input signal having a different range of in-band component to out-band component ratios without saturating and without having a signal-to-noise ratio approaching one. The method further includes providing a plurality of switches, each one for controllably connecting and disconnecting the output of a respective one of the signal processors to the system output terminal. The method also includes detecting the strength of the respective output signal at each one of at least one selected output of the signal processors to compare the strength of the respective output signal with at least one limit to select one of the signal processors for optimal processing of the input signal. Finally, the method includes causing a respective one of the switches to connect the output of the selected signal processors to the signal output and causing other ones of the switches to disconnect the outputs of all other signal processors from the system output. 
       
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS  
       [0006]    Further objects, features, and advantages of the invention will become apparent from the following detailed description taken in conjunction with the accompanying figures showing illustrative embodiments of the invention, in which:  
         [0007]    [0007]FIG. 1 is a block diagram illustrating a prior art signal processing system;  
         [0008]    [0008]FIG. 2 is a block diagram illustrating a signal processing system in accordance with the present invention;  
         [0009]    [0009]FIG. 3 is a block diagram illustrating still another signal processing system in accordance with the present invention;  
         [0010]    [0010]FIG. 4 is a block diagram illustrating yet another signal processing system in accordance with the present invention;  
         [0011]    [0011]FIG. 5( a ) is a block diagram illustrating a still further signal processing system in accordance with the present invention;  
         [0012]    [0012]FIG. 5( b ) is a block diagram illustrating an additional signal processing system in accordance with the present invention;  
         [0013]    [0013]FIG. 6 is a block diagram illustrating a further additional signal processing system in accordance with the present invention;  
         [0014]    [0014]FIG. 7( a ) is a block diagram illustrating a first filter bank in accordance with the present invention;  
         [0015]    [0015]FIG. 7( b ) is a block diagram illustrating a second filter bank in accordance with the present invention;  
         [0016]    [0016]FIG. 7( c ) is a block diagram illustrating a third filter bank in accordance with the present invention;  
         [0017]    [0017]FIG. 8 is a circuit diagram illustrating a Tow-Thomas biquad in accordance with the present invention;  
         [0018]    [0018]FIG. 9 is a circuit diagram illustrating a transconductor in accordance with the present invention;  
         [0019]    [0019]FIG. 10 is a circuit diagram illustrating an additional biquad in accordance with the present invention;  
         [0020]    [0020]FIG. 11 is a circuit diagram illustrating a peak detector and a threshold detector in accordance with the present invention;  
         [0021]    [0021]FIG. 12( a ) is a block diagram illustrating an additional signal strength detector in accordance with the present invention;  
         [0022]    [0022]FIG. 12( b ) is a block diagram illustrating an additional signal strength detector in accordance with the present invention;  
         [0023]    [0023]FIG. 13 is a circuit diagram illustrating a timer in accordance with the present invention;  
         [0024]    [0024]FIG. 14( a ) is a block diagram illustrating a further additional signal processing circuit in accordance with the present invention;  
         [0025]    [0025]FIG. 14( b ) is a block diagram illustrating a further additional signal processing circuit in accordance with the present invention;  
         [0026]    [0026]FIG. 15 is a block diagram illustrating a further additional signal processing circuit in accordance with the present invention;  
         [0027]    [0027]FIG. 16 is a circuit diagram illustrating a biquad in accordance with the present invention;  
         [0028]    [0028]FIG. 17 is a circuit diagram illustrating a dynamic input scaling unit in accordance with the present invention;  
         [0029]    [0029]FIG. 18 is a circuit diagram illustrating a dynamic output scaling unit in accordance with the present invention;  
         [0030]    [0030]FIG. 19 is a circuit diagram illustrating a portion of a bias selector in accordance with the present invention;  
         [0031]    [0031]FIG. 20 is a circuit diagram illustrating a portion of a bias selector in accordance with the present invention;  
         [0032]    [0032]FIG. 21 is a block diagram illustrating a further additional signal strength detector in accordance with the present invention;  
         [0033]    [0033]FIG. 22 is a circuit diagram illustrating an on-off transconductor in accordance with the present invention. 
     
    
       [0034]    Throughout the figures, unless otherwise stated, the same reference numerals and characters are used to denote like features, elements, components, or portions of the illustrated embodiments. Moreover, while the subject invention will now be described in detail with reference to the figures, and in connection with the illustrative embodiments, changes and modifications can be made to the described embodiments without departing from the true scope and spirit of the subject invention as defined by the appended claims.  
       DETAILED DESCRIPTION OF THE INVENTION  
       [0035]    [0035]FIG. 1 illustrates an example of a prior art signal processing system  100 . The signal processing system  100  is a companding filter. A companding filter amplifies or attenuates an input signal that is applied to a filter circuit, and attenuates or amplifies the output signal from the circuit. The prior art companding filter  100  includes an input  102 , a signal strength detector  104 , an input variable gain amplifier  106 , a main filter  108 , an output variable gain amplifier  110 , and an output  112 .  
         [0036]    The input  102  of the signal processing system  100  corresponds to input  101  of the signal strength detector  104  and an input  120  of the input variable gain amplifier  106 . The input variable gain amplifier  106  amplifies or attenuates the signal received by the input  120  depending on a gain control input signal received at a gain control input  103  of the input variable gain amplifier  106  and outputs the resultant signal at its output  105 . The output  105  of the input variable gain amplifier  106  corresponds to input  107  of the main filter  108 . The main filter  108  processes the signal received at the input  107  and produces an output signal at its output  109 . The output  109  of the main filter  108  corresponds to input  111  of the output variable gain amplifier  110 . The output variable gain amplifier  110  amplifies or attenuates the signal received at the input  111  depending on a gain control signal received at a gain control input  113  of the output variable gain amplifier  110  and outputs the resultant signal at its output  112 . The gain of the output variable gain amplifier  110  is the inverse of the gain of the input variable gain amplifier  106 . The output  114  of the output variable gain amplifier  110  is connected to the output  112  of the signal processing system  100 .  
         [0037]    The signal strength detector  104  measures the strength (e.g., the voltage envelope) of the signal applied to the input  101  of the signal strength detector  104  and outputs a gain control signal at its output  115 , which is connected to the gain control inputs  103  and  113  of the input variable gain amplifier  106  and the output variable gain amplifier  110 , respectively. Depending on the strength of the signal at the input  101  of the signal strength detector  104 , different gain control signals are provided at the output  115  of the signal strength detector  104 . If the signal applied to the input  101  of the signal strength detector  104  is small, the gain control signal should be large causing the signal applied to the input  102  of the signal processing system  100  to be amplified before it is applied to the main filter  108 , such that the signal is large compared to the filter noise, i.e. the noise generated by the filter. If the signal applied to the input  101  of the signal strength detector  104  is large, the gain control signal should be small causing the signal applied to the input  102  of the signal processing system  100  to be slightly amplified or even attenuated before it is applied to the signal processing circuit  108  to avoid saturating the main filter  108 .  
         [0038]    [0038]FIG. 2 illustrates an example of a signal processing system  200 . The signal processing system  200  generates a processed signal with a strong in channel component well above the filter noise. The signal processing system  200  includes three banks of filters in parallel with each other. The first bank of filters includes a plurality of filters  202 ,  220 ,  232 , a plurality of amplifiers  214 ,  226  and a first bank switch  238 . The second bank of filters includes a plurality of filters  204 ,  222 ,  234 , a plurality of amplifiers  216 ,  228  and a second bank switch  240 . The third bank of filters includes a plurality of filters  206 ,  224 ,  236 , a plurality of amplifiers  218 ,  230  and a third bank switch  242 .  
         [0039]    It is noted that a different number of filter banks may be used, and each one of the filter banks may have more or fewer filters and associated amplifiers.  
         [0040]    A signal received by the input  201  of the signal processing system  200  which typically includes an in-band component and an out-band component, is conveyed to an input  203  of the filter  202  of the first filter bank. Preferably, the filter  202  has enough linear range to accommodate the in-band component and the out-band component of the signal without saturating. The filter  202  processes the signal received at its input  203  and outputs a processed signal at its output  209 . The output  209  of the filter  202  corresponds to input  215  of the amplifier  214 . The amplifier  214  is a fixed gain amplifier, which amplifies the signal received at its input  215  and produces an output signal at its output  221 . The output  221  of the amplifier  214  corresponds to input  227  of the filter  220 . The filter  220  processes the signal received at its input  227  and outputs a processed signal at its output  233 . The output  233  of the filter  220  corresponds to input  239  of the amplifier  226 . The amplifier  226  is a fixed gain amplifier, which amplifies the signal it receives at its input  239  and produces an output signal at its output  245 . The output  245  of the amplifier  226  corresponds to input  251  of the filter  232 . The filter  232  processes the signal received at its input  251  and outputs a processed signal at its output  257 . The output  257  of the filter  232  corresponds to input  263  of the switch  238 . An output  275  of the switch  238  is connected to the output  244  of the signal processing system  200 .  
         [0041]    The signal received by the input  201  of the signal processing system  200  is also conveyed to an input  205  of the filter  204  of the second filter bank. Preferably, the filter  204  has enough linear range to accommodate the in-band component and the out-band component of the signal without saturating. The filter  204  processes the signal received at its input  205  and provides a processed signal at its output  211 . The output  211  of the filter  204  corresponds to input  217  of the amplifier  216 . The amplifier  216  is a fixed gain amplifier, which amplifies the signal received at its input  217  and produces an amplified signal at its output  223 . The output  223  of the amplifier  216  corresponds to input  229  of the filter  222 . The filter  222  processes the signal received at its input  229  and outputs a processed signal at its output  235 . The output  235  of the filter  222  corresponds to input  241  of the amplifier  228 . The amplifier  228  is a fixed gain amplifier, which amplifies the signal received at its input  241  and produces an amplified signal at its output  247 . The output  247  of the amplifier  228  corresponds to input  253  of the filter  234 . The filter  234  processes the signal received at its input  253  and outputs a processed signal at its output  259 . The output  259  of the filter  234  corresponds to input  265  of the switch  240  and to an input  271  of the signal strength detector  208 . An output  277  of the switch  240  is connected to the output  244  of the signal processing system  200 .  
         [0042]    The signal received by the input  201  of the signal processing system  200  is also conveyed to an input  207  of the filter  206  of the third filter bank. Preferably, the filter  206  has enough linear range to accommodate the in-band component and the out-band component of the signal without saturating. The filter  206  processes the signal received at its input  207  and outputs a processed signal at its output  213 . The output  213  of the filter  206  corresponds to input  231  of the amplifier  218 . The amplifier  218  is a fixed gain amplifier, which amplifies the signal received at its input  219  and produces an amplified signal at its output  225 . The output  225  of the amplifier  218  corresponds to input  231  of the filter  224 . The filter  224  processes the signal received at its input  231  and provides a processed signal at its output  237 . The output  237  of the filter  224  corresponds to input  243  of the amplifier  230 . The amplifier  230  is a fixed gain amplifier, which amplifies the signal received at its input  243  and produces an amplified signal at its output  249 . The output  249  of the amplifier  230  corresponds to input  255  of the filter  236 . The filter  236  processes the signal received at its input  255  and outputs a processed signal at its output  261 . The output  261  of the filter  236  corresponds to input  267  of the switch  242 . The output  279  of the switch  242  is connected to the output  244  of the signal processing system  200 .  
         [0043]    Preferably, the filters  202 ,  204 ,  206  have the same transfer function; the filters  220 ,  222 ,  224  have the same transfer function; and the filters  232 ,  234 ,  236  have the same transfer function.  
         [0044]    Each filter bank should be optimized to effectively process signals with a different in-band component/out-band component ratio. The first filter bank is optimized for input signals having a large out-band component and a relatively small in-band component. The first filter bank is optimized by having the amplifiers  214 ,  226  have a gain of more than one. Preferably, the amplifiers  214 ,  226  have gains of ten so that each amplifier provides a signal with ten times the amplitude of the input signal. The second bank is optimized for input signals having an out-band component which is slightly larger than the in-band component. The second filter bank is optimized by having the amplifier  216  have a gain of one, and having the amplifier  228  have a gain greater than one. Preferably, the amplifier  228  has a gain of ten, causing the amplifier  228  to provide a signal at its output  247  with ten times the amplitude of the signal received at its input  241 . The third bank is optimized for input signals having an out-band component that is approximately equal to the in-band component. The third filter bank is optimized by having the amplifiers  218 ,  230  each have a gain substantially equal to one. Preferably, the amplifiers  214 ,  216 ,  218 ,  226 ,  228  and  230  are clamped such that they will not provide any of the filters  220 ,  222 ,  224 ,  232 ,  234  and  236 , respectively, with an input signal that will saturate the filter.  
         [0045]    The signal strength detector  208  selects the filter bank that is the most suitable for processing the signal received by the input  201  of the signal processing system  200 . An input  271  of the signal strength detector  208  is connected to the output  259  of the filter  234 , and outputs  281 ,  283 ,  285  of the signal strength detector  208  are connected to the switch control inputs  287 ,  289 ,  291  of the switches  238 ,  240 ,  242 , respectively. The signal strength detector  208  can detect the voltage envelope of the signal on the output  259  of the filter  234 . A low-pass-filtered rectifier, well-known for use in many other applications, is one example of a circuit which can be used as an envelope detector. The signal strength detector  208  determines if the voltage envelope of the output  259  of the filter  234  exceeds a first limit whereby the output signal of the filter is approaching the minimum tolerable signal to noise ratio of the filter, or a second limit whereby the filter is entering saturation. In the exemplary embodiment of the signal processing system  200  the first, second and third filter banks are designed such that there exists a first limit representing the point where the first filter bank is near saturation and the output signal of the second filter bank is near the minimum tolerable signal to noise ratio of the second filter bank, and a second limit representing the point where the second filter bank is near saturation and the output signal of the third filter bank is near the minimum tolerable signal to noise ratio of the third filter bank.  
         [0046]    If the signal strength detector  208  detects that the voltage envelope of the signal at the output  259  of the filter  234  does not exceed the first limit or the second limit, the signal strength detector  208  selects the first filter bank by providing a logical one on its output  281  to cause the switch  238  to close and a logical zero on its outputs  283 ,  285  to cause the switches  240 ,  242 , respectively, to open, thereby connecting the first filter bank to the output  244  of the signal processing system  200  and disconnecting the second filter bank and the third filter bank from the output  244 . For purposes of the specification and claims, positive logic is assumed. If the signal strength detector  208  detects that the voltage envelope of the signal at the output  259  of the filter  234  exceeds the first limit but not the second limit, the signal strength detector  208  selects the second filter bank by providing a logical one on its output  283  to cause the switch  240  to close and a logical zero on its outputs  281 ,  285  to cause the switches  238 ,  242 , respectively, to open, thereby connecting the second filter bank to the output  244  of the signal processing system  200  and disconnecting the first filter bank and the third filter bank from the output  244 . If the signal strength detector  208  detects that the voltage envelope of the signal at the outputs  259  of the filter  234  exceeds the first limit and the second limit, the signal strength detector  208  selects the third filter bank by providing a logical one on its output  285  to cause the switch  242  to close and logical zero on its outputs  281 ,  283  to cause the switches  240 ,  242 , respectively, to open, thereby connecting the third filter bank to the output  244  of the signal processing system  200  and disconnecting the first filter bank and the second filter bank from the output  244 .  
         [0047]    In an alternate exemplary embodiment, the signal strength detector  208  measures the strengths of the signals at other nodes in the signal processing system  200 . The signal strength detector  208  may, for example, measure the voltage envelopes of the signals on outputs  233 ,  235 ,  237  of the filters  220 ,  222 ,  224 , respectively.  
         [0048]    In another alternate exemplary embodiment, the first, second and third banks of filters, and associated amplifiers, shown in FIG. 2, can each be replaced by a respective sixth order bandpass Chebychev filters  700 ,  730 ,  760 , shown in FIGS.  7 ( a ),  7 ( b ),  7 ( c ), respectively. The sixth order bandpass Chebychev filter  700  of FIG. 7( a ) advantageously has a ripple of 0.25 dB, a bandwidth of 0.5 MHz, and a center frequency of 1.25 Mhz. The sixth order bandpass Chebychev filter  730  of FIG. 7( b ) advantageously has a ripple of 0.25 dB, a bandwidth of 0.5 MHz, and a center frequency of 1.25 MHz. The sixth order bandpass Chebychev filter  760  of FIG. 7( c ) advantageously has a ripple of 0.25 dB, a bandwidth of 0.5 MHz, a center frequency of 1.25 MHz. Preferably, each of the sixth order bandpass Chebychev filters  700 ,  730 ,  760  can be implemented by connecting three standard Tow-Thomas biquads  800  together in series.  
         [0049]    [0049]FIG. 8 illustrates the standard Tow-Thomas biquad circuit  800 . The Tow-Thomas biquad  800  includes a transconductor  808 , a transconductor  824 , a transconductor  834 , a transconductor  844 , a capacitor  816 , and a capacitor  854 . The center frequency ω 0  of the Tow-Thomas biquad  800  can be calculated by the equation:  
         ω 0   =QG   m   /C   (1)  
         [0050]    where Q is the quality factor of the Tow-Thomas biquad circuit  800 . The absolute value of the transconductors and capacitors can be scaled by the same factor, i.e. impedance scaling, without affecting the transfer function of the Tow-Thomas biquad  800 , since the transfer function depends on the ratios between these values. Impedance scaling does not change the transfer function of the Tow-Thomas biquad  800 , however it does change the power dissipation and the noise level of the Tow-Thomas biquad  800 .  
         [0051]    A signal received by the input  802  of the Tow-Thomas biquad  800  is conveyed to a positive input  804  of a transconductor  808 . The transconductor  808  processes the difference between the signal received at the positive input  804  and the signal received at a negative input  806 , which is connected to ground, and provides a signal at an output  810 . The signal at the output  810  is equal to the difference in the signal received by the positive input  804  and the signal received by the negative input  806  of the transconductor  808 , scaled by a transconductance G in  of the transconductor  808 . The transconductance G in  of the transconductor  808  sets the gain of the biquad  800 , for example, if G in  is ten times G m , the effective input amplification for the biquad  800  is ten. The output  810  of the transconductor  808  is connected to a terminal  814  of the capacitor  816 , a negative input  822  of a transconductor  824 , an output  830  of the transconductor  824 , a positive input  832  of the transconductor  834 , an output  850  of the transconductor  844 , and the output  812  of the Tow-Thomas biquad  800 . These connections form a node  860 . The other terminal  818  of the capacitor  816  is connected to ground. The capacitor  816  integrates the currents provided at node  860 .  
         [0052]    The transconductor  824  processes the difference between the signal received at a positive input  826 , which is connected to ground, and the signal received at the negative input  822  and provides a signal at the output  830 . The signal at the output  830  of the transconductor  824  is equal to the difference in the signal received by its positive input  826  and the signal received by its negative input  822 , scaled by its transconductance G m . The output  830  of the transconductor  824  is connected to one terminal  814  of a capacitor  816 , the negative input  822  of the transconductor  824 , the output  830  of the transconductor  824 , the positive input  832  of the transconductor  834 , the output  850  of the transconductor  844 , and the output  812  of the Tow-Thomas biquad  800 . The transconductor  824  forms a feedback loop with the node  860 .  
         [0053]    The transconductor  834  processes the difference between the signal received at its positive input  832  and the signal received at its negative input  836 , which is connected to ground, and provides a signal at an output  840 . The signal at the output  840  is equal to the difference in the signal received by the positive input  832  and the signal received by the negative input  836 , scaled by a transconductance QG m . The output  840  of the transconductor  834  is connected to one terminal  852  of a capacitor  854  and a negative input  842  of the transconductor  844 . The other terminal  856  of the capacitor  854  is connected to ground.  
         [0054]    The transconductor  844  processes the difference between the signal received at its positive input  846 , which is connected to ground, and the signal received at its negative input  842  and provides a signal at an output  850 . The signal at the output  850  is equal to the difference in the signal received by the positive input  846  and the signal received by the negative input  842  of the transconductor  844 , scaled by a transconductance QG m . The output  850  of the transconductor  844  is connected to on terminal  814  of the capacitor  816 , the negative input  822  of the transconductor  824 , the output  830  of the transconductor  824 , the positive input  832  of the transconductor  834 , and the output  812  of the Tow-Thomas biquad  800 . The transconductors  834 ,  844  and the capacitor  854  form a feedback loop to the node  860 .  
         [0055]    In an exemplary embodiment of the Tow-Thomas biquad  800 , a first diode and a second diode are connected to the node  860 . The cathode of the first diode is connected to the node  860 , and an anode of the first diode is connected to ground. The anode of the second diode is connected to the node  860 , and a cathode of the second diode is connected to ground. This arrangement limits the voltage swing at the node  860  to approximately ±0.7 volts.  
         [0056]    In another exemplary embodiment of the Tow-Thomas biquad  800 , a first diode and a second diode are connected to the input  804 . The cathode of the first diode is connected to the input  804 , and an anode of the first diode is connected to ground. The anode of the second diode is connected to the input  804 , and a cathode of the second diode is connected to ground. This arrangement limits the voltage swing at the input  804  to approximately ±0.7 volts.  
         [0057]    In still another embodiment of the Tow-Thomas biquad  800 , a first diode and a second diode are connected to the output  840 . The cathode of the first diode is connected to the output  840 , and an anode of the first diode is connected to ground. The anode of the second diode is connected to the output  840 , and a cathode of the second diode is connected to ground. This arrangement limits the voltage swing at the output  840  to approximately ±0.7 volts.  
         [0058]    [0058]FIG. 9 illustrates the transconductor  808  in greater detail. The transconductors  808 ,  826 ,  834  and  844  are similar in construction. The transconductor  808  includes an NMOS transistor Q 1 , an NMOS transistor Q 2 , a PMOS transistor Q 3 , a PMOS transistor Q 4 , an NMOS transistor Q 5 , an NMOS transistor Q 6 , and a current source  924 .  
         [0059]    A signal received by the positive input  804  of the transconductor  808  is conveyed to the gate  905  of the NMOS transistor Q 1 . The NMOS transistor Q 1  allows current to flow from its source  907  to its drain  906 , or vice versa, depending on the signal at the gate  905  and the relative voltages at its source  907  and at its drain  906 . The drain  906  of the NMOS transistor Q 1  is connected to the drain  913  and the gate  911  of the PMOS transistor Q 3 , and the gate  914  of the PMOS transistor Q 4 . The source  907  of the NMOS transistor Q 1  is connected to the drain  918  of the NMOS transistor Q 5 , and the source  910  of the NMOS transistor Q 2 .  
         [0060]    A signal received by the negative input  806  of the transconductor  808  is conveyed to a gate  908  of the NMOS transistor Q 2 . The drain  909  of the NMOS transistor Q 2  is connected to the drain  916  of the PMOS transistor Q 4  and is the output  810  of the transconductor  808 . The source  910  of the NMOS transistor Q 2  is connected to the drain  918  of the NMOS transistor Q 5 , and the source  907  of the NMOS transistor Q 1 .  
         [0061]    The drain  913  of the PMOS transistor Q 3  is connected to the drain  906  of the NMOS transistor Q 1 , the gate  911  of the PMOS transistor Q 3 , and the gate  914  of the PMOS transistor Q 4 . The source  912  of the PMOS transistor Q 3  is connected to supply voltage V dd . The gate  911  of the PMOS transistor Q 3  is connected to the drain  906  of the NMOS transistor Q 1 , the drain  913  of the PMOS transistor Q 3 , and the gate  914  of the PMOS transistor Q 4 .  
         [0062]    The drain  916  of the PMOS transistor Q 4  is connected to the drain  909  of the NMOS transistor Q 2 , and the output  810  of the transconductor  808 . The source  912  of the PMOS transistor Q 3  is connected to supply voltage V dd . The gate  914  of the PMOS transistor Q 4  is connected to the drain  906  of the NMOS transistor Q 1 , the drain  913  and the gate  911  of the PMOS transistor Q 3 .  
         [0063]    The drain  918  of the NMOS transistor Q 5  is connected to the source  907  of the NMOS transistor Q 1  and the source  910  of the NMOS transistor Q 2 . The source  919  of the NMOS transistor Q 5  is connected to supply voltage V ss . The gate  917  of the NMOS transistor Q 5  is connected to the gate  920  and the drain  921  of the NMOS transistor Q 6 , and the positive terminal  925  of the current source  924 .  
         [0064]    The drain  921  of the NMOS transistor Q 6  is connected to the gate  920  of the NMOS transistor Q 6 , the gate  917  of the NMOS transistor Q 5 , and the positive terminal  925  of the current source  924 . The source  922  of the NMOS transistor Q 6  is connected to supply voltage V ss . The gate  920  of the NMOS transistor Q 6  is connected to the gate  917  of the NMOS transistor Q 5 , the drain  921  of the NMOS transistor Q 6 , and the negative terminal  925  of the current source  924 .  
         [0065]    The current source  924  produces a bias current Ibias for the transconductor  808 . The bias current Ibias produced by the current source  924  controls the center frequency of the filter. The bias current Ibias of the transconductor  808  is adjusted to give a stable center frequency in the presence of fabrication tolerances and temperature variations. The bias current Ibias can be any value, for example 100 micro-amperes, and the transistors Q 1 , Q 2 , Q 3 , Q 4 , Q 5 , Q 6  of the transconductor  808  are scaled to yield the desired transconductances. The transconductance for the transconductors is calculated using the equation:  
           G   m   =I   tail /( V   GS   −V   T ),  (2)  
         [0066]    where I tail  is the current passing through the transistor Q 5  of the transconductor  808 , V T  is the threshold voltage of the to transistors Q 5 , Q 6 , and V GS  is the gate-source voltage of the transistors Q 5 , Q 6 . The linear range of the transconductor is related to the quantity V GS −V T . Once the bias current Ibias has been set, the transistors Q 5 , Q 6  are scaled such that, the following equation is satisfied:  
         ( W   Q5   /L   Q5 )/( W   Q6   /L   Q6 )= I   tail   /I   bias   (3)  
         [0067]    The negative terminal  925  of the current source  924  is connected to the drain  921  and the gate  920  of the transistor Q 6 , and the gate  917  of the transistor Q 5 . The positive terminal of the current source  924  is connected to supply voltage V dd . The preferred form of the current source  924  is a resistor connected to the between the supply voltage V dd  and the drain  921  and the gate  920  of the NMOS transistor Q 6 .  
         [0068]    Referring to FIG. 7( a ), a signal received by the input  702  of the sixth order bandpass Chebychev filter  700  of the first filter bank is conveyed to an input  704  of a Tow-Thomas biquad  706 . The Tow-Thomas biquad  706  processes the signal received at its input  704  and provides a signal at its output  708 . Advantageously, the Tow-Thomas biquad  706  has a transconductance G in  for transconductor  808  of 771 micro-amperes per volt, transconductance G m  for a transconductor  824  of 185 micro-amperes per volt, a transconductance QG m  for transconductors  834  and  844  of 591 micro-amperes per volt, and a capacitance for capacitors  816 ,  854  of 77 picofarads. The output  708  of the Tow-Thomas biquad  706  corresponds to input  710  of a Tow-Thomas biquad  712 .  
         [0069]    In the alternative, the Tow-Thomas biquad  706  can be optimized to use less power. To optimize the Tow-Thomas biquad  706  to use less power, the transconductance G in  for the transconductor  808  can be 979 micro-amperes per volt, the transconductance G m  for the transconductor  824  can be 235 micro-amperes per volt, the transconductance QG m  for transconductors  834  and  844  can be 750 micro-amperes per volt, and the capacitance for capacitors  816 ,  854  can be 97.5 picofarads.  
         [0070]    The Tow-Thomas biquad  712  processes the signal received at its input  710  and provides a signal at its output  714 . Advantageously, the Tow-Thomas biquad  712  has a transconductance G in  for the transconductor  808  of 2312 micro-amperes per volt, a transconductance G m  for the transconductor  824  of 185 micro-amperes per volt, a transconductance QG m  for the transconductors  834  and  844  of 1210 micro-amperes per volt, and a capacitance for the capacitors  816 ,  854  of 196 picofarads. The output  714  of the Tow-Thomas biquad  712  corresponds to input  716  of a Tow-Thomas biquad  718 .  
         [0071]    In the alternative, the Tow-Thomas biquad  712  can be optimized to use less power. To optimize the Tow-Thomas biquad  712  to use less power, the transconductance G in  for the transconductor  808  can be 294 micro-amperes per volt, the transconductance G m  for the transconductor  824  can be 23.5 micro-amperes per volt, the transconductance QG m  for the transconductors  834  and  844  can be 154 micro-amperes per volt, and the capacitance for the capacitors  816 ,  854  can be 25 picofarads.  
         [0072]    The Tow-Thomas biquad  718  processes the signal received at its input  716  and provides a signal at its output  720 . The Tow-Thomas biquad  718  has a transconductance G in  for the transconductor  808  of 971 micro-amperes per volt, a transconductance G m  for the transconductor  824  of 185 micro-amperes per volt, a transconductance QG m  for the transconductors  834  and  844  of 1210 micro-amperes per volt, and a capacitance for the capacitors  816 ,  854  of 126 picofarads. The output  720  of the Tow-Thomas biquad  718  corresponds to output  722  of the sixth order bandpass Chebychev filter  700 .  
         [0073]    In the alternative, the Tow-Thomas biquad  718  can be optimized to use less power. To optimize the Tow-Thomas biquad  718 , the transconductance G in  for the transconductor  808  can be 123 micro-amperes per volt, the transconductance Gm for the transconductor  824  can be 23.5 micro-amperes per volt, the transconductance QG m  for the transconductors  834  and  844  can be 154 micro-amperes per volt, and the capacitance for the capacitors  816 ,  854  can be 16 picofarads.  
         [0074]    Referring to FIG. 7( b ), a signal received by the input  732  of the sixth order bandpass Chebychev filter  730  of the second filter bank is conveyed to an input  734  of a Tow-Thomas biquad  736 . The Tow-Thomas biquad  736  processes the signal received at its input  734  and provides a signal at its output  738 . Advantageously, the Tow-Thomas biquad  736  has a transconductance G in  for the transconductor  808  of 9.29 micro-amperes per volt, a transconductance G m  for the transconductor  824  of 2.23 micro-amperes per volt, a transconductance QG m  for the transconductors  834  and  844  of 7.12 micro-amperes per volt, and a capacitance for the capacitors  816 ,  854  of 0.9252 picofarads. The output  738  of the Tow-Thomas biquad  736  corresponds to input  740  of a Tow-Thomas biquad  742 .  
         [0075]    The Tow-Thomas biquad  742  processes the signal received at its input  740  and provides a signal at its output  744 . Advantageously, the Tow-Thomas biquad  742  has a transconductance G in  for the transconductor  808  of 9.29 micro-amperes per volt, a transconductance G m  for the transconductor  824  of 2.23 micro-amperes per volt, a transconductance QG m  for the transconductors  834  and  844  of 14.59 micro-amperes per volt, and a capacitance for the capacitors  816 ,  854  of 2.3664 picofarads. The output  744  of the Tow-Thomas biquad  742  corresponds to input  746  of a Tow-Thomas biquad  748 .  
         [0076]    The Tow-Thomas biquad  748  processes the signal received at its input  746  and provides a signal at its output  750 . Advantageously, the Tow-Thomas biquad  748  has a transconductance G in  for the transconductor  808  of 9 micro-amperes per volt, a transconductance G m  for the transconductor  824  of 2.23 micro-amperes per volt, a transconductance QG m  for the transconductors  834  and  844  of 14.59 micro-amperes per volt, and a capacitance for the capacitors  816 ,  854  of 1.5191 picofarads. The output  750  of the Tow-Thomas biquad  748  corresponds to output  752  of the sixth order bandpass Chebychev filter  730 .  
         [0077]    Referring to FIG. 7( c ), a signal received by the input  762  of the sixth order bandpass Chebychev filter  760  of the third filter bank is conveyed to an input  764  of a Tow-Thomas biquad  766 . The Tow-Thomas biquad  766  processes the signal received at its input  764  and provides a signal at its output  768 . The Tow-Thomas biquad  766  includes a transconductance G in  for the transconductor  808  of 0.7292 micro-amperes per volt, a transconductance G m  for the transconductor  824  of 0.7 micro-amperes per volt, a transconductance QG m  for the transconductors  834  and  844  of 2.2349 micro-amperes per volt, and a capacitance for the capacitors  816 ,  854  of 0.2904 picofarads. The output  768  of the Tow-Thomas biquad  766  corresponds to input  770  of a Tow-Thomas biquad  772 .  
         [0078]    The Tow-Thomas biquad  772  processes the signal received at its input  770  and provides a signal at its output  774 . The Tow-Thomas biquad  772  includes a transconductance G in  for the transconductor  808  of 1.1438 micro-amperes per volt, a transconductance G m  for the transconductor  824  of 0.7 micro-amperes per volt, a transconductance QG m  for the transconductors  834  and  844  of 4.58 micro-amperes per volt, and a capacitance for the capacitors  816 ,  854  of 0.7428 picofarads. The output  74  of the Tow-Thomas biquad  772  corresponds to input  776  of a Tow-Thomas biquad  778 .  
         [0079]    The Tow-Thomas biquad  778  processes the signal received at its input  776  and provides a signal at its output  780 . The Tow-Thomas biquad  778  includes a transconductance G in  for the transconductor  808  of 2.8269 micro-amperes per volt, a transconductance G m  for the transconductor  824  of 0.7 micro-amperes per volt, a transconductance QG m  for the transconductors  834  and  844  of 4.58 micro-amperes per volt, and a capacitance for the capacitors  816 ,  854  of 0.4769 picofarads. The output  780  of the Tow-Thomas biquad  778  corresponds to output  782  of the sixth order bandpass Chebychev filter  760 .  
         [0080]    Referring to FIG. 12( a ), there is shown an exemplary embodiment of a signal strength detector  1200 , which may be used as the signal strength detector  208  in the signal processing circuit  200  illustrated in FIG. 2. The signal strength detector  1200  has an input  1202  corresponding to the input  271  of the signal strength detector  208 , and the outputs  1240 ,  1242 ,  1244 , corresponding to the outputs  281 ,  283 ,  285  of the signal strength detector  208 , respectively.  
         [0081]    The signal strength detector  1200  senses the voltage envelope of the input signals received at the input  1202 , and selects an appropriate signal processing circuit given two threshold limits. The first threshold limit represents a point at which the first filter bank is near saturation and the output signal of the second filter bank is near its minimum tolerable signal to noise ratio. The second threshold limit represents the point at which the second filter bank is near saturation and the output signal of the third filter bank is near its minimum tolerable signal to noise ratio. The signal strength detector  1200  includes a peak detector  1180 , a first threshold detector  1175 , a second threshold detector  1176 , a two input NOR gate  1228 , a two input AND gate  1230 , and a two input AND gate  1232 . The peak detector  1180  and the first threshold detector  1175  are described in more detail below in relation to FIG. 11.  
         [0082]    A signal received at the input  1202  of the signal strength detector  1200  is conveyed to an input  1204  of the peak detector  1180 . The peak detector  1180  processes the signal received at the input  1204  and provides a signal at an output  1206  of the peak detector  1180 . The signal output at the output  1206  is conveyed to an input  1208  of the first threshold detector  1175  and an input  1210  of the second threshold detector  1176 . The first threshold detector  1175  processes the signal received at its input  1208  and provides a signal at an output  1212 . The first threshold detector  1175  transmits a logical one on the output  1212  if the signal at the input  1208  exceeds the first threshold limit, and a logical zero on the output  1212  if the signal at the input  1208  does not exceed the first threshold limit. The signal output at the output  1212  of the first threshold detector  1175  is conveyed to an input  1216  of the two input NOR gate  1228 , an input  1220  of the two input AND gate  1230 , and an input  1224  of the two input AND gate  1232 . The second threshold detector  1176  processes the signal received at its input  1210  and provides a signal at an output  1214 . The second threshold detector  1176  transmits a logical one on the output  1212  if the signal at the input  1208  exceeds the second threshold limit, and a logical zero on the output  1212  if the signal at the input  1208  does not exceed the second threshold limit. The signal output at the output  1214  of the second threshold detector  1176  is conveyed to the other input  1218  of the two input NOR gate  1228 , an inverted input  1222  of the two input AND gate  1230 , and the other input  1226  of the two input AND gate  1232 .  
         [0083]    The two input NOR gate  1228  processes the signals received at its input  1216  and its input  1218 , and provides a signal at the output  1234 . The output  1234  is connected to the output  1240  of the signal strength detector  1200 . The two input AND gate  1230  processes the signals received at its input  1220  and its inverted input  1222 , and provides a signal at the output  1236 . The output  1236  is connected to the output  1242  of the signal strength detector  1200 . The two input AND gate  1232  processes the signals received at its input  1224  and its input  1226 , and provides a signal at the output  1238 . The output  1238  is connected to the output  1244  of the signal strength detector  1200 .  
         [0084]    [0084]FIG. 11 illustrates a portion  1100  of the signal strength detector  1200  of FIG. 12 in greater detail. The signal strength detector portion  1100  includes the peak detector  1180  and the first threshold detector  1175 . The peak detector  1180  includes an NMOS transistor Q 1 , a PMOS transistor Q 3 , an NMOS transistor Q 4 , a PMOS transistor Q 5 , a PMOS transistor Q 6 , a capacitor  1173 , and a transconductor  1107 .  
         [0085]    A signal received by the input  1102  of the peak detector  1180  is conveyed to a positive input  1103  of the transconductor  1107 . The transconductor  1107  processes the difference between the signal received at its positive input  1103  and a signal received at its negative input  1105 , which is connected to ground, and provides a signal at an output  1109 . The signal at the output  1109  is equal to the difference in the signal received by the positive input  1103  and the signal received by the negative input  1105 , scaled by a transconductance G in  of the transconductor  1107 . The transconductor  1107  has a transconductance G m  of 1 miliampere per volt. The signal provided at the output  1109  of the transconductor  1107  is conveyed the gate  1104  of the PMOS transistor Q 3 , the gate  1106  of the NMOS transistor Q 4 , the gate  1108  of the PMOS transistor Q 5 , the drain  1110  of the PMOS transistor Q 5 , the source  1112  of the PMOS transistor Q 6 , the backgate  1114  of the PMOS transistor Q 6 , and a drain  1116  of the NMOS transistor Q 1 . The PMOS transistor Q 3  and the NMOS transistor Q 4  form an inverter receiving the signal received by the input  1102 . The source  1118  of the PMOS transistor Q 3  is connected to supply voltage V dd . The gate  1104  of the PMOS transistor Q 3  is connected to the input  1102 , the gate  1106  of the NMOS transistor Q 4 , the gate  1108  of the PMOS transistor Q 5 , the drain  1110  of the PMOS transistor Q 5 , the source  1112  of the PMOS transistor Q 6 , the backgate  1114  of the PMOS transistor Q 6 , and the drain  1116  of the NMOS transistor Q 1 . The backgate  1120  of the PMOS transistor Q 3  is connected to supply voltage Vdd, and the drain  1122  of the PMOS transistor Q 3  is connected to the drain  1124  of the NMOS transistor Q 4 , the source  1130  of the PMOS transistor Q 5  and the gate  1134  of the PMOS transistor Q 6 . The source  1128  of the NMOS transistor Q 4  is connected to supply voltage V ss . The gate  1106  of PMOS transistor Q 4  is connected to the input  1102 , the gate  1104  of the PMOS transistor Q 3 , the gate  1108  of the PMOS transistor Q 5 , the drain  1110  of the PMOS transistor Q 5 , the source  1112  of the PMOS transistor Q 6 , the backgate  1114  of the PMOS transistor Q 6 , and the drain  1116  of the NMOS transistor Q 1 . The backgate  1126  of the NMOS transistor Q 4  is connected to supply voltage V ss . The drain  1124  of the NMOS transistor Q 4  is connected to the drain  1122  of the PMOS transistor Q 3 , the source  1130  of the PMOS transistor Q 5  and the gate  1134  of the PMOS transistor Q 6 .  
         [0086]    The PMOS transistor Q 5  is connected to act as a diode for the signal received at the input  1102  of the peak detector  1180 . The gate  1108  and the drain  1110  of the PMOS transistor Q 5  are connected to each other, the input  1102 , the gate  1104  of the PMOS transistor Q 3 , the gate  1106  of the NMOS transistor Q 4 , the source  1112  of the PMOS transistor Q 6 , the backgate  1114  of the PMOS transistor Q 6 , and the drain  1116  of the NMOS transistor Q 1 . The backgate  1132  of the PMOS transistor Q 5  is connected to supply voltage V dd . The source  1130  of the PMOS transistor Q 5  is connected to the drain  1122  of the PMOS transistor Q 3 , the drain  1124  of the NMOS transistor Q 4  and the gate  1134  of the PMOS transistor Q 6 .  
         [0087]    The PMOS transistor Q 6  acts as a PMOS switch for the signal at the input  1102  of the peak detector  1180 . The gate  1134  of the PMOS transistor Q 6  is connected to the source  1130  of the PMOS transistor Q 5 , the drain  1122  of the PMOS transistor Q 3 , and the drain  1124  of the NMOS transistor Q 4 . The source  1112  and the backgate  1114  of the PMOS transistor Q 6  are connected to each other, the input  1102 , the gate  1108  of the PMOS transistor Q 5 , the drain  1110  of the PMOS transistor Q 5 , the gate  1104  of the PMOS transistor Q 3 , the gate  1106  of the NMOS transistor Q 4 , and the drain  1116  of the NMOS transistor Q 1 . The drain  1136  of the PMOS transistor Q 6  is connected to a gate  1138  of the NMOS transistor Q 1 , an output  1172  of the peak detector  1180 , and a terminal  1171  of the capacitor  1173 . A terminal  1181  of the capacitor  1173  is connected to supply voltage V ss .  
         [0088]    The NMOS transistor Q 1  of the peak detector  1180  forms half of an NMOS current mirror that acts as a current memory which stores the peak current of the signal received at the input  1102  of the peak detector  1180 . The other half of the NMOS current mirror that acts as a current memory is the NMOS transistor Q 2  of a threshold detector  1175  connected to the output  1172  of the peak detector  1180 . The source  1144  of the NMOS transistor Q 1  is connected to supply voltage V ss . The gate of the NMOS transistor Q 1  is connected to the output  1172  of the peak detector  1180  and the drain  1136  of the PMOS transistor Q 6 . The backgate  1142  of the NMOS transistor Q 1  is connected to supply voltage V ss . And the drain  1116  of the NMOS transistor Q 1  is connected to the input  1102 , the source  1112  of the PMOS transistor Q 6 , the backgate  1114  of the PMOS transistor Q 6 , the gate  1108  and drain  1110  of the PMOS transistor Q 5 , the gate  1104  of the PMOS transistor Q 3 , and the gate  1106  of the NMOS transistor Q 4 .  
         [0089]    The first threshold detector  1175  compares the voltage envelope of a signal received at the input  1102  of the peak detector  1180  to a reference current supplied by a current source  1170 . The first threshold detector  1175  includes an NMOS transistor Q 2 , a PMOS transistor Q 7 , a PMOS transistor Q 8 , the current source  1170 , a PMOS transistor Q 9 , and an NMOS transistor Q 10 . Any number of threshold detectors can be connected to the peak detector  1180  to derive a corresponding number of signal strength detector outputs. A signal received by the input  1174  of the first threshold detector  1175  is conveyed to the gate  1140  of the NMOS transistor Q 2 .  
         [0090]    The NMOS transistor Q 2  of the first threshold detector  1175  forms half of an NMOS current mirror that acts as a current memory which stores the peak current corresponding to the voltage signal received at the input  1102  of the peak detector  1180 . The other half of the NMOS current mirror that acts as a current memory consists of the NMOS transistor Q 1  of the peak detector  1180  connected to the input  1174  of the first threshold detector  1175 . The source  1146  of the NMOS transistor Q 2  is connected to supply voltage V ss . The drain  1150  of the NMOS transistor Q 2  is connected to the gate  1153  of the PMOS transistor Q 9 , the gate  1159  of the NMOS transistor Q 10 , and the drain  1154  of a PMOS transistor Q 7 . The gate  1140  of the NMOS transistor Q 2  is connected to the input  1174  of the first threshold detector  1175 . The backgate  1148  of the NMOS transistor Q 2  is connected to supply voltage V ss .  
         [0091]    The NMOS transistor Q 9  and the NMOS transistor Q 10  form an inverter. The gate  1153  of the PMOS transistor Q 9  is connected to the gate  1159  of the NMOS transistor Q 10 , the drain  1154  of the NMOS transistor Q 7 , and the drain  1150  of the NMOS transistor Q 2 . The source  1155  of the PMOS transistor Q 9  is connected to supply voltage V dd . The drain  1157  of the PMOS transistor Q 9  is connected to the drain  1161  of the NMOS transistor Q 10  and the output  1152  of the first threshold detector  1175 . The source  1163  of the NMOS transistor Q 10  is connected to supply voltage V ss . The drain  1161  of the NMOS transistor Q 10  is connected to the drain  1157  of the PMOS transistor Q 9  and the output  1152  of the first threshold detector  1175 .  
         [0092]    The NMOS transistor Q 7 , an NMOS transistor Q 8  and the current source  1170  form a current mirror that causes a current to flow through the NMOS transistor Q 7  that mirrors the current of the current source  1170 . The gate  1158  of the NMOS transistor Q 7  is connected to the gate  1162  of the NMOS transistor Q 8 , the drain  1164  of the NMOS transistor Q 8 , and the positive terminal  1166  of the current source  1170 . The source  1156  of the NMOS transistor Q 7  is connected to supply voltage V dd  and the source  1160  of the NMOS transistor Q 8 . The drain  1154  of the NMOS transistor Q 7  is connected to the gate  1153  of the PMOS transistor Q 9 , the gate  1159  of the NMOS transistor Q 10 , and the drain  1150  of the NMOS transistor Q 2 . The gate  1162  and the drain  1164  of the NMOS transistor Q 8  are connected to each other, the gate of the NMOS transistor Q 7  and the positive terminal  1166  of the current source  1170 . The source  1160  of the NMOS transistor Q 5  is connected to the source  1156  of the NMOS transistor Q 7  and supply voltage V dd . The current source  1170  includes a positive terminal  1166  and a negative terminal  1168 . The positive terminal  1166  of the current source  1170  is connected to the gate  1158  of the NMOS transistor Q 7 , the gate  1162  of the NMOS transistor Q 8 , and the drain  1164  of the NMOS transistor Q 5 . The negative terminal  1168  of the current source  1170  is connected to ground.  
         [0093]    The current source  1170  produces a reference current that represents the threshold voltage of the first threshold detector  1175 . The current can be any value, for example 100 uA, and the transistors Q 7 , Q 8  of the first threshold detector  1175  are scaled to yield the desired current through the transistor Q 7 . The preferred form of a current source is a resistance connected between the drain of NMOS transistor Q 8  and ground. In the present example the reference current generated by the current source in the first threshold detector  1175  is 7.7 micro-amperes.  
         [0094]    The output  1152  of the first threshold detector  1175  indicates which filter bank should be used given the voltage envelope of the signal received at the input  1102  of the peak detector  1180 . If the current flowing through the transistor Q 2 , which represents the voltage envelope of the signal received at the input  1102  of the peak detector  1180 , exceeds the current flowing through the transistor Q 7 , which is related to the reference current of the current source  1170 , the output  1152  of the first threshold detector  1175  would be a logical one. If the current flowing through the transistor Q 2  does not exceed the current flowing through the transistor Q 7 , the output  1152  of the first threshold detector  1175  would be a logical zero. In this manner, the first threshold limit of the signal strength detector  1200  is current generated by the current source  1170 .  
         [0095]    The second threshold detector  1176  (not shown in FIG. 11) may be similar to the first threshold detector  1175  as shown in FIG. 11. It would have a counterpart to NMOS transistor Q 2  of the first threshold detector  1175 , with the gate of the counterpart transistor connected to the output  1172  of the peak detector  1180 . The second threshold detector  1176  would also have its counterpart to the current mirror, which in the first threshold detector  1175  consists of NMOS transistors Q 7  and Q 8 , and reference current source  1170 . The counterpart to the current source  1170  of the second threshold detector  1176  would produce a reference current that represents the second threshold limit. In the present example, the counterpart to the current source  1170  would generate 77 micro-amperes.  
         [0096]    Referring to FIG. 2, the signal processing system  200  can have more than three filter banks. If the filter system  200  includes more than three filter banks, the signal strength detector  208  must be adapted to select an appropriate filter bank from the more than three filter banks. In order to select the appropriate filter bank from a signal processing system with more than three filter banks, the signal strength detector may be modified to have a group of peak detectors, each similar to the peak detector  1180  shown in FIG. 11, to sense the voltage envelope of the output signal provided by each of the filter banks of the system  200 , except for the filter bank configured to process the largest input signal range and the filter bank configured to process the smallest input signal range. For example, if the filter system  200  has five filter banks, a filter bank configured to process the largest input signals, a filter bank configured to process the smallest input signals, and a group of three filter banks configured to process intermediate input signals, the voltage envelopes of the output signals produced by the group of three intermediate signal filter banks are measured by the signal strength detector. Assuming that the filter banks are designed such that the saturation level of each filter bank, except the largest signal filter bank, overlaps the minimum tolerable signal to noise ratio of another filter bank, the signal strength detector has three threshold detectors, preferably similar to the first threshold detector  1175  shown in FIG. 11, to compare the voltage envelope of the output signal of each one of the three intermediate signal filter banks with a corresponding first threshold limit. Each first threshold limit indicates when the corresponding filter bank is approaching saturation. For example, if the signal strength detector measures the voltage envelopes of the signals of the three intermediate signal filter banks, three threshold detectors are needed to compare the detected envelopes with three different first threshold limits. The strength detector also uses an additional threshold detector, preferably similar to the first threshold detector  1175  shown in FIG. 11, to compare the voltage envelope of the output signal from the filter bank configured to process the smallest input signals with a second threshold limit. The second threshold limit indicates when the output signal of the smallest signal filter bank is approaching its saturation point. Once the voltage envelopes of the output signals the three intermediate signal filter banks and the smallest signal filter bank are compared to respective first and second threshold limits, the strength detector selects the filter bank that is configured to process the smallest input signal without saturating.  
         [0097]    In an alternate embodiment of the signal processing system  200  of FIG. 2, the respective gains of amplifiers  216 ,  218 ,  230  each have a first selected value and the respective gains of amplifiers  214 ,  226 ,  228  each have a second selected value. The filters  202 ,  204 ,  206  each have the same transfer function; and the filters  222 ,  224  each have the same transfer function. This allows the signal processing system  200  to have an alternate structure shown in FIG. 3.  
         [0098]    A signal received by the input  301  of the signal processing system  300 , which include an in-band component and an out-band component, is conveyed to an input  303  of a filter  302 . Preferably, the filter  302  has enough linear range to accommodate the signal on the input  301  of the signal processing system  300  without saturating. The filter  302  processes the signal received at its input  303  and produces a processed signal at its output  305 . The output  305  of the filter  302  corresponds to input  307  of an amplifier  314  and an input  309  of an amplifier  316 . The amplifier  314  amplifies or attenuates the signal received at its input  307  and provides an amplified signal at its output  311 . The output  311  of the amplifier  314  corresponds to input  315  of a filter  320 . The filter  320  processes the signal received at its input  315  and produces a processed signal at its output  319 . The output  319  of the filter  320  corresponds to input  323  of an amplifier  326 . The amplifier  326  amplifies or attenuates the signal received at its input  323  and outputs an amplified signal at its output  329 . The output  329  of the amplifier  326  corresponds to input  335  of a filter  332 . The filter  332  processes the signal received at its input  335  and produces a processed signal at its output  341 . The output  341  of the filter  332  corresponds to input  347  of a switch  338 . The switch  338  outputs the signal received at its input  347  on its output  353  when the signal received at its switch control input  361  is a logical one, and isolates its input  347  from its output  353  when the signal received at its switch control input  361  is a logical zero. The output  353  of the switch  338  is connected to the output  344  of the signal processing system  300 .  
         [0099]    The amplifier  316  amplifies or attenuates the signal received at its input  309  and outputs an amplified signal at its output  313 . The output  313  of the amplifier  316  corresponds to input  317  of a filter  322 . The filter  322  processes the signal received at its input  317  and produces a processed signal at its output  321 . The output  321  of the filter  322  corresponds to input  325  of an amplifier  328  and an input  327  of an amplifier  330 . The amplifier  328  amplifies or attenuates the signal received at its input  325  and provides an amplified signal at its output  331 . The output  331  of the amplifier  328  corresponds to input  337  of a filter  334 . The filter  334  processes the signal received at its input  337  and produces a processed signal at its output  343 . The output  343  of the filter  334  corresponds to input  349  of a switch  340  and an input  375  of the signal strength detector  308 . The switch  340  outputs the signal received at its input  349  on its output  355  when the signal received at its switch control input  363  is a logical one, and does not output the signal received at its input  349  on its output  355  when the signal received at its switch control input  363  is a logical zero. The output  355  of the switch  340  is connected to the output  344  of the signal processing system  300 .  
         [0100]    The amplifier  330  amplifies or attenuates the signal received at its input  327  and outputs an amplified signal at its output  333 . The output  333  of the amplifier  330  corresponds to input  339  of a filter  336 . The filter  336  processes the signal received at its input  339  and produces a processed signal at its output  345 . The output  345  of the filter  336  corresponds to input  351  of a switch  342 . The switch  342  outputs the signal received at its input  351  on its output  357  when the signal received at its switch control input  365  is a logical one, and does not output the signal received at its input  351  on its output  357  when the signal received at its switch control input  365  is a logical zero. The output  357  of the switch  342  is connected to the output  344  of the signal processing system  300 .  
         [0101]    Preferably, the signal processing system  300  is optimized such that the signal processing pathways that terminate at outputs  341 ,  343 ,  345  of the filters  332 ,  334 ,  336 , respectively, are each adapted for a different in-band component/out-band component ratio. The signal processing pathways that terminate at the output  341  of the filter  332  is adapted for processing an input signal that has a large out-band component and a relatively small in-band component. This signal processing path is so adapted by having the respective gains of amplifiers  314 ,  326  to be greater than one. Preferably, the amplifiers  314 ,  326  have respective gains of ten so that each amplifier provides a signal with ten times the amplitude of the signal at its input. The signal processing path that terminates at the output  343  of the filter  334  is adapted for processing an input signal that has an out-band component which is slightly larger than the in-band component. This signal processing path is so adapted by having the gains of the amplifier  316  equal to one, and having the gain of amplifier  328  greater than one. Preferably, the amplifier  328  has a gain of ten, causing the amplifier  328  to provide a signal at its output  331  with ten times the amplitude of the signal received at its input  325 . The signal processing path that terminates at the output  345  of the filter  336  is adapted to process an input signal that has an out-band component that is approximately equal to the in-band component. This signal processing path is so adapted by having the respective gains of amplifiers  316 ,  330  each equal to one. Preferably, the amplifiers  314 ,  316 ,  326 ,  328  and  330  are clamped such that they will not provide any of the filters  320 ,  322 ,  332 ,  334  and  336  with an input signal that will saturate the filter.  
         [0102]    The signal strength detector  308  analyzes the voltage envelope of the signal received on its input  375  to determine if the voltage envelope of the signal received on the input  375  exceeds or is below respective limits whereby the filter  334  is entering saturation or the signal received at the input  375  is approaching the minimum tolerable signal to noise ratio of the filter  334 . For the filter system  300 , there can be two limits. A first limit represents the point where the filter  332  is near saturation and the filter  334  is near the minimum tolerable signal to noise ratio. A second limit represents the point where the filter  334  is near saturation and the filter  336  is near the minimum tolerable signal to noise ratio.  
         [0103]    If the signal strength detector  308  detects that the voltage envelope of the signal received at its input  375  does not exceed the first limit or the second limit, the signal strength detector  308  selects the signal that was processed by the filter  332  by providing a logical one on its output  367  to close the switch  338  and a logical zero on its outputs  369 ,  371  to open the switches  340 ,  342 , respectively. In this manner, the signal from the output  341  of the filter  332  is provided to the output  344  of the signal processing system  300 , and the outputs  343 ,  345  of the filters  334 ,  336 , respectively, are disconnected from the output  344  of the signal processing system  300 . If the signal strength detector  308  detects that the voltage envelope of the signal received at the input  375  of the signal strength detector  308  falls below the second limit, but exceeds the first limit, the signal strength detector  308  selects the signal that was processed by the filter  334  by providing a logical one on its output  369  to close the switch  340  and a logical zero on its outputs  367 ,  371  to open the switches  338 ,  342 , respectively, thereby connecting the signal from the output  343  of the filter  334  to the output  344  of the signal processing system  300  and disconnecting the outputs  341 ,  345  of the filters  332 ,  336  from the output  344  of the signal processing system  300 . If the signal strength detector  308  detects that the voltage envelope of the signal received at the input  375  of the signal strength detector  308  exceeds the first limit and the second limit, the signal strength detector  308  selects the signal that was processed by the filter  336  by providing a logical one on its output  371  to close the switch  342  and a logical zero on its outputs  367 ,  369  to open the switches  338 ,  340 , respectively, thereby connecting the signal from the output  345  of the filter  336  to the output  344  of the signal processing system  300  and disconnecting the outputs  341 ,  343  of the filters  332 ,  334  from the output  344  of the signal processing system  300 .  
         [0104]    In an exemplary embodiment, the signal strength detector  1200  of FIG. 12( a ) may be used as the signal strength detector  308 . Referring the FIG. 12( a ), the input  1202  of the signal strength detector  1200  may serve as input  375  of the signal strength detector  308  in FIG. 3, and the outputs  1240 ,  1242 ,  1244  of the signal strength detector  1200  may serve as outputs  367 ,  369  and  371  of the signal strength detector  308  of FIG. 3, respectively. In addition, the threshold detector  1175  may be adjusted to reflect the first limit, while the threshold detector  1176  may be adjusted to reflect the second limit.  
         [0105]    [0105]FIG. 4 illustrates another exemplary signal processing system  400  according to the present invention. The signal processing system  400  includes multiple companding signal processors  434 ,  436 ,  438  with different fixed input and output gains configured in parallel with each other. A signal received by an input  402  of the signal processing system  400  is conveyed to an input  401  of the companding signal processor  434 , an input  403  of the companding signal processor  436 , an input  405  of the companding signal processor  438 , and an input  452  of a signal strength detector  410 .  
         [0106]    The signal received by the input  401  of the companding signal processor  434  corresponds to input  407  of an amplifier  404 . The amplifier  404  amplifies or attenuates the signal received at its input  407  and produces an output signal at its output  415 . The gain of the amplifier  404  is fixed at a first amplification level. The output  415  of the amplifier  404  corresponds to input  421  of the filter  414 . The filter  414  processes the signal received at its input  421  and outputs a processed signal at its output  427 . The output  427  of the filter  414  corresponds to input  435  of the amplifier  420 . The amplifier  420  amplifies or attenuates the signal received at its input  435  and produces an output signal at its output  443 . The gain of the amplifier  420  is fixed at an inverse of the first amplification level. The output  443  of the amplifier  420  is connected to the input  455  of a switch  426 . The switch  426  outputs the signal received at its input  455  on its output  461  when a signal received at its switch control input  467  is a logical one, and does not output the signal received at its input  455  on its output  461  when the signal received at its switch control input  467  is a logical zero. The output  461  of the switch  426  is connected to the output  432  of the signal processing system  400 .  
         [0107]    The signal received by the input  403  of the companding signal processor  436  corresponds to input  409  of an amplifier  406 . The amplifier  406  amplifies or attenuates the signal received at its input  409  and produces an output signal at its output  417 . The gain of the amplifier  406  is fixed at a second amplification level. The output  417  of the amplifier  406  corresponds to input  423  of a filter  416 . The filter  416  processes the signal received at its input  423  and provides a processed signal at its output  429 . The output  429  of the filter  416  is connected to the input  437  of an amplifier  422 . The amplifier  422  amplifies or attenuates the signal received at its input  437  and produces an output signal at its output  445 . The gain of the amplifier  422  is fixed at an inverse of the second amplification level. The output  445  of the amplifier  422  corresponds to input  457  of the switch  428 . The switch  428  outputs the signal received at its input  457  on its output  463  when the signal received at its switch control input  469  is a logical one, and does not output the signal received at its input  457  on its output  463  when the signal received at its switch control input  469  is a logical zero. The output  463  of the switch  428  is connected to the output  432  of the signal processing system  400 .  
         [0108]    The signal received by the input  405  of the companding signal processor  438  corresponds to input  411  of an amplifier  408 . The amplifier  408  amplifies or attenuates the signal received at its input  411  and produces an output signal at its output  419 . The gain of the amplifier  408  is fixed at a third amplification level. The output  419  of the amplifier  408  corresponds to input  425  of the filter  418 . The filter  418  processes the signal received at its input  425  and outputs a processed signal at its output  431 . The output  431  of the filter  418  corresponds to input  439  of the amplifier  424 . The amplifier  424  amplifies or attenuates the signal received at its input  439  and produces an output signal at its output  447 . The gain of the amplifier  424  is fixed at an inverse of the third amplification level. The output  447  of the amplifier  424  is connected to the input  459  of a switch  430 . The switch  430  outputs the signal received at its input  459  on its output  465  when a signal received at its switch control input  471  is a logical one, and does not output the signal received at its input  459  on its output  465  when the signal received at its switch control input  471  is a logical zero. The output  465  of the switch  430  is connected to the output  432  of the signal processing system  400 .  
         [0109]    The first companding signal processor  434  is configured to process signals with a larger signal voltage envelope than the second companding signal processor  436  and the third companding signal processor  438 . Moreover, the corresponding signal processors are advantageously designed such that the saturation level of each companding signal processor except for the one designed to process the largest signals, overlaps the minimum tolerable signal to noise ratio of another one of the companding signal processors. The second companding signal processor  436  is configured to process signals with a smaller signal voltage envelope than the first companding signal processor  434  and a larger signal voltage envelope than the third companding signal processor  438 . The third companding signal processor  438  is configured to process signals with a smaller signal voltage envelope than the first companding signal processor  434  and the second companding signal processor  436 . Preferably, the first companding signal processor  434 , the second companding signal processor  436 , and the third companding signal processor  438  are each adapted to effectively process a signal over a different signal amplitude range. In one exemplary embodiment, the transfer functions of the filter  414 ,  416 ,  418  are the same, and the first amplification level, the second amplification level and the third amplification level are different. Preferably, the first amplification level is greater than the second amplification level which is greater than the third amplification level.  
         [0110]    The signal strength detector  410  selects the one of the companding signal processors  434 ,  436 ,  438  that has the most suitable saturation level and minimum tolerable signal to noise ratio for processing the signal received by the input  402  of the signal processing system  400 , which is connected to the input  452  of the signal strength detector  410 . Only one of the companding filters  434 ,  436 ,  438  is selected by the signal strength detector  410  at any one time. The signal strength detector  410  analyzes the signal received at the input  402  to determine if the voltage envelope of the signal received at the input  402  exceeds a first limit whereby the signal received at the input  402  is approaching the minimum tolerable signal to noise ratio of the companding signal processor  436  and a second limit whereby the companding signal processor  436  is entering saturation. The first limit representing the point where the signal received at the input  402  is near the minimum tolerable signal to noise ratio of the companding filter  436  and the companding filter  434  is near saturation, and the second limit representing the point where the companding filter  436  is near saturation and the signal received at the input  402  is near its minimum tolerable signal to noise ratio. A low-pass-filtered rectifier, well-known for use in many other applications, is one example of a circuit which can be used as an envelope detector.  
         [0111]    The signal strength detector  410  selects the first companding signal processor  434  if the voltage envelope of the signal received by the input  402  does not exceed the first limit or the second limit. The signal strength detector  410  selects the first companding signal processor  434  by providing a logical one on an output  473  of the signal strength detector  410 , and a logical zero on outputs  475 ,  477  of the signal strength detector  410 . The signal strength detector  410  selects the second companding signal processor  436  if the voltage envelope of the signal received by the input  402  is above the first limit but below the second limit. The signal strength detector  410  selects the second companding signal processor  436  by providing a logical one on an output  475  of the signal strength detector  410 , and a logical zero on the outputs  473 ,  477  of the signal strength detector  410 . The signal strength detector  410  selects the third companding signal processor  438  if the voltage envelope of the signal received by the input  402  is above the first limit and the second limit. The signal strength detector  410  selects the third companding signal processor  438  by providing a logical one on an output  477  of the signal strength detector  410 , and a logical zero on the outputs  473 ,  475  of the signal strength detector  410 . The outputs  473 ,  475 ,  477  of the signal strength detector  410  are connected to the switch control inputs  467 ,  469 ,  471 , respectively, of the switches  426 ,  428 ,  430 .  
         [0112]    In an alternate exemplary embodiment, the amplifiers  404 ,  406 ,  408  are clamped such that they will not provide any of the filters  414 ,  416 ,  418  with an input signal that will saturate the filter.  
         [0113]    In an exemplary embodiment, the companding signal processor  434  of the filter  400  of FIG. 4 may be implemented as a biquad  1000 , shown in FIG. 10, with a bandwidth of 100 kHz. The biquad  1000  can have a center frequency of 2 MHz and a quality factor of 20. The biquad  1000  can be optimized for relatively small input signals by having a relatively large effective amplification at the input of the biquad and a commensurately large effective attenuation at the output of the biquad  1000 . The biquad  1000  processes the signal received at the input  401  and provides a signal at the output  455 . Referring to FIG. 10, the biquad  1000  may advantageously have a transconductance G in  for a transconductor  1008  of 500 micro-amperes per volt, a transconductance G m  for a transconductors  1024  and  1062  of 50 micro-amperes per volt, a transconductance QG m  for transconductors  1034  and  1044  of 1000 micro-amperes per volt, a capacitance for capacitors  1016 ,  1054  of 80 picofarads, and a resistance for a resistor  1068  of 2 KΩ or 1/G in .  
         [0114]    In the exemplary embodiment, the companding signal processor  436  of the filter  400  of FIG. 4 may be implemented as a biquad  1000 , shown in FIG. 10, advantageously having a bandwidth of 100 kHz. The biquad  1000  can advantageously have a center frequency of 2 MHz and a quality factor of 20. The biquad  1000  can advantageously be optimized for average input signals by having little or no effective amplification at the input of the biquad and a commensurate effective attenuation at the output of the biquad  1000 . The biquad  1000  processes the signal received at the input  403  and provides a signal at the output  457 . Referring to FIG. 10, the biquad  1000  may advantageously have a transconductance G in  for the first transconductor  1008  of 50 micro-amperes per volt, a transconductance G m  for the transconductors  1024  and  1062  of 50 micro-amperes per volt, a transconductance QG m  for the transconductors  1034  and  1044  of 1000 micro-amperes per volt, a capacitance for the capacitors  1016 ,  1054  of 80 picofarads, and a resistance for the resistor  1068  of 20 KΩ or 1/G in .  
         [0115]    In the exemplary embodiment, the companding signal processor  438  of the filter  400  of FIG. 4 can be implemented as a biquad  1000 , shown in FIG. 10, advantageously having a bandwidth of 100 kHz. The biquad  1000  can advantageously have a center frequency of 2 MHz and a quality factor of 20. The biquad  1000  can advantageously be optimized for relatively large input signals by having relatively large attenuation at the input of the biquad and a commensurate effective amplification at the output of the biquad  1000 . The biquad  1000  processes the signal received at the input  405  and provides a signal at the output  459 . Referring to FIG. 10, the biquad  1000  advantageously has a transconductance G in  for the first transconductor  1008  of 5 micro-amperes per volt, a transconductance G m  for the transconductors  1024  and  1062  of 50 micro-amperes per volt, a transconductance QG m  for the transconductors  1034  and  1044  of 1000 micro-amperes per volt, a capacitance for the capacitors  1016 ,  1054  of 80 picofarads, and a resistance for the resistor  1068  of 200 KΩ or 1/G in .  
         [0116]    [0116]FIG. 10 illustrates an exemplary biquad  1000  suitable for implementing the companding filter  434 ,  436  and  438  of the signal processor  400  of FIG. 4. The biquad  1000  includes a first transconductor  1008 , a second transconductor  1024 , a third transconductor  1034 , a fourth transconductor  1044 , a fifth transconductor  1062 , a first capacitor  1016 , a second capacitor  1054 , and a resistor  1068 . The center frequency of the biquad  1000  can be calculated by equation (1). The absolute value of the transconductors and capacitors can be scaled by the same factor, i.e. impedance scaling, without affecting the transfer function of the biquad  1000 , since the transfer function depends on the ratios between these values. Impedance scaling does not change the transfer function of the biquad  1000 , however it does change the power dissipation and the noise level of the biquad  1000 .  
         [0117]    A signal received by the input  1002  of the biquad  1000  is conveyed to a positive input  1004  of the first transconductor  1008  of the biquad  1000 . The first transconductor  1008  processes the difference between the signal received at its positive input  1004  and a signal received at its negative input  1006 , which is connected to ground, and provides a signal at an output  1010 . The signal at the output  1010  is equal to the difference in the signal received by the positive input  1004  and the signal received by the negative input  1006 , scaled by a transconductance G in  of the first transconductor  1008 . The first transconductance G in  of the first transconductor  1008  sets the gain of the biquad, for example, if G in  is ten times G m  the effective input amplification for the biquad  1000  is ten. The output  1010  of the first transconductor  1008  is connected to one terminal  1014  of the first capacitor  1016 , a negative input  1022  of the second transconductor  1024 , an output  1030  of the second transconductor  1024 , a positive input  1032  of the third transconductor  1034 , and an output  1050  of the fourth transconductor  1044 . These connections form a first node  1074 . The other terminal of the first capacitor  1016  is connected to ground. The first capacitor  1016  integrates the signals provided at the first node  1074 .  
         [0118]    The second transconductor  1024  processes the difference between the signal received at its positive input  1026 , which is connected to ground, and the signal received at its negative input  1022  and provides a signal at its output  1030 . The signal at the output  1030  is equal to the difference in the signal received by the positive input  1026  and the signal received at the negative input  1022 , scaled by a transconductance G m  of the second transconductor  1024 . The output  1030  of the second transconductor  1024  is connected to one terminal  1014  of the first capacitor  1016 , the negative input  1022  of the second transconductor  1024 , the output  1030  of the second transconductor  1024 , the positive input  1032  of the third transconductor  1034 , and the output  1050  of the fourth transconductor  1044 . The second transconductor  1024  forms a feedback loop with the first node  1074 .  
         [0119]    The third transconductor  1034  processes the difference between the signal received at the positive input  1032  and the signal received at its negative input  1036 , which is connected to ground, and provides a signal at an output  1040 . The signal at the output  1040  is equal to the difference in the signal received by its positive input  1032  and the signal received by its negative input  1036 , scaled by a transconductance QG m  of the third transconductor  1034 . The output  1040  of the third transconductor  1034  is connected to one terminal  1052  of the second capacitor  1054 , a negative input  1042  of the fourth transconductor  1044 , and a positive input  1058  of the fifth transconductor  1062 . These connections form a second node  1076 . The other terminal  1056  of the second capacitor  1054  is connected to ground.  
         [0120]    The fourth transconductor  1044  processes the difference between the signal received at its positive input  1046 , which is connected to ground, and the signal received at its negative input  1042  and provides a signal at the output  1050 . The signal at its output  1050  is equal to the difference in the signal received by the positive input  1046  and the signal received by the negative input  1042 , scaled by a transconductance QG m  of the fourth transconductor  1044 . The output  1050  of the fourth transconductor  1044  is connected to one terminal  1014  of the first capacitor  1016 , the negative input  1022  of the second transconductor  1024 , the output  1030  of the second transconductor  1024 , and the positive input  1032  of the third transconductor  1034 . The third and fourth transconductors  1034 ,  1044  and the second capacitor  1054  form a feedback loop with the second node  1076 .  
         [0121]    The fifth transconductor  1062  processes the difference between the signal received at its positive input  1058 , and the signal received at its negative input  1060 , which is connected to ground, and provides a signal at an output  1064 . The signal at the output  1064  is equal to the difference in the signal received by the positive input  1058  and the signal received by the negative input  1060  of the fifth transconductor  1062 , scaled by a transconductance QG m  of the fifth transconductor  1062 . The output  1064  of the fifth transconductor  1062  is connected to one terminal  1066  of the resistor  1068  and the output  1072  of the biquad  1000 . An other terminal  1070  of the resistor  1068  is connected to ground. The resistor  1068 , together with the transconductor  1062 , creates an amplifier at the output of the biquad  1000  resulting in an effective output amplification or attenuation.  
         [0122]    In another exemplary embodiment, a first diode and a second diode are connected to the first node  1074 . The cathode of the first diode is connected to the first node  1074 , and an anode of the first diode is connected to ground. The anode of the second diode is connected to the first node  1074 , and a cathode of the second diode is connected to ground. This arrangement limits the voltage swing at the first node  1074  to approximately ±0.7 volts.  
         [0123]    In further exemplary embodiment, a first diode and a second diode are connected to the second node  1076 . The cathode of the first diode is connected to the second node  1076 , and an anode of the first diode is connected to ground. The anode of the second diode is connected to the second node  1076 , and a cathode of the second diode is connected to ground. This arrangement limits the voltage swing at the second node  1076  to approximately ±0.7 volts.  
         [0124]    In another embodiment, a first diode and a second diode are connected to the input  1004 . The cathode of the first diode is connected to the input  1004 , and an anode of the first diode is connected to ground. The anode of the second diode is connected to the input  1004 , and a cathode of the second diode is connected to ground. This arrangement limits the voltage swing at the input  1004  to approximately 0.7 volts.  
         [0125]    In an exemplary embodiment of the signal processing system  400  of FIG. 4, the signal strength detector  410  can be implemented by using the signal strength detector  1200  shown in FIG. 12. Referring to FIG. 12( a ), the input  1202  of the signal strength detector  1200  may serve as the input  434  of the signal strength detector  410  and the outputs  1240 ,  1242 ,  1244  of the signal strength detector  1200  mat serve as the outputs  477 ,  475 ,  473  of the signal strength detector  410 , respectively. Also, the first threshold detector  1175  may be adjusted to reflect the first limit, and the second threshold detector  1176  may be adjusted to reflect the second limit. The reference current of the current source  1170  of the first threshold detector  1175  can be 11 micro-amperes, and the reference current of the current source  1170  of the second threshold detector  1176  can be 110 micro-amperes.  
         [0126]    [0126]FIG. 5( a ) illustrates a signal processing system  500  according to another exemplary embodiment of the present invention. The characteristics of the signal processing system  500  can be changed dynamically. The signal processing system  500  includes an input  502 , a first signal processing circuit  514 , a second signal processing circuit  530 , a signal strength detector  556 , a bias selector  566 , a timer  588 , a first switch  540 , a second switch  548  and an output  594 .  
         [0127]    A signal received by the input  502  of the signal processing system  500  is conveyed to an input  504  of the first signal processing circuit  514 , and an input  520  of the second signal processing circuit  530 . The first signal processing circuit  514  includes the input  504 , an input  506 , an input  508 , an input  510 , a power input  512 , an output  516  and an output  518 . The first signal processing circuit  514  processes the signal received at its input  504  based on respective signals received at the inputs  506 ,  508 ,  510 ,  512 , and outputs processed signals at its outputs  516 ,  518 . The signal processing circuit  514  can be turned on and off by a signal applied to its power input  512 . If a logical high signal is received at the power input  512 , the first signal processing circuit  514  is turned on. Conversely, if a logical zero signal is received at the power input  512 , the first signal processing circuit  514  is turned off. The output  516  of the first signal processing circuit  514  corresponds to input  552  of the signal strength detector  556 . The output  518  of the first signal processing circuit  514  corresponds to input  536  of the first switch  540 . The first switch  540  outputs the signal received at its input  536  on its output  542  when the signal received at its switch control input  538  is a logical one, and isolates its input  536  from its output  542  when the signal received at its switch control input  538  is a logical zero. The output  542  of the first switch  540  is connected to the output  594  of the signal processing system  500 .  
         [0128]    The second signal processing circuit  530  includes the input  520 , an input  522 , an input  524 , an input  526 , a power input  528 , an output  532  and an output  534 . The second signal processing circuit  530  processes the signal received at its input  520  based on respective signals received at the inputs  522 ,  524 ,  526 ,  528 , and outputs processed signals at its outputs  532 ,  534 . The second signal processing circuit  530  can be turned on and off by a signal applied to the input  528 . If a logical high signal is received at the power input  528 , the second signal processing circuit  530  is turned on. Conversely, if a logical zero signal is received at the power input  528 , the second signal processing circuit  530  is turned off. The output  532  of the second signal processing circuit  530  corresponds to input  554  of the signal strength detector  556 . The output  534  of the second signal processing circuit  530  corresponds to input  544  of the second switch  548 . The second switch  548  outputs the signal received at its input  544  on its output  550  when the signal received at its switch control input  546  is a logical one, and isolates its input  544  from its output  550  when the signal received at its switch control input  546  is a logical zero. The output  550  of the second switch  548  is connected to the output  594  of the signal processing system  500 .  
         [0129]    The signal strength detector  556  selects the most suitable bias for the inactive signal processing circuit  514  or  530  (i.e., the one of the first and second signal processing circuits  514 ,  530  that does not have its output  518 ,  534  connected to the system output  594 ) for processing the signal received from an internal node of the active signal processing circuit (i.e., the one of the first and second signal processing circuits  514 ,  530  having its output  518 ,  534  connected to the system output  594 ) of the signal processing circuits  514 ,  530  at the inputs  552 ,  554  of the signal strength detector  556  based on the voltage envelope of the signal received from the active signal processing circuit  514  or  530 . The amplitude or envelope signal can be derived using an envelope detector. A low-pass-filtered rectifier, well-known for use in many other applications, is one example of a circuit which can be used as an envelope detector. The first and second signal processing circuits  514  and  530  can be biased so that the signal processing circuits  514 ,  530  have a high effective range, (i.e., the filter works in a satisfactory way for a range of large signals between saturation and the noise floor of the filter) with a third bias, a medium effective range (i.e., the filter works in a satisfactory way for a range of medium signals between saturation and the noise floor of the filter), with a second bias, and a low effective range (i.e., the filter works in a satisfactory way for a range of small signals between saturation and the noise floor of the filter), with a first bias. The signal strength detector  556  selects the appropriate bias based upon a first limit and a second limit. The second limit indicates the onset of saturation of the active signal processing circuit. The first limit indicates that the signal from the internal node of the active signal processing circuit  514  or  530  is approaching the minimum tolerable signal to noise ratio of the active signal processing circuit  514  or  530 . The outputs  558 ,  560  the signal strength detector  556  indicate the appropriate bias as determined by the strength detector  556 . The signal strength detector  556  drives the output  558  to a logical zero and the output  560  to a logical zero if the voltage envelope of the signal received from the active signal processing circuit  514  or  530  does not exceed the first limit or the second limit. The signal strength detector  556  drives the output  558  to a logical zero and the output  560  to a logical one if the voltage envelope of the signal received from the active signal processing circuit  514  or  530  exceeds the first limit but does not exceed the second limit. And, the strength detector  556  drives the output  558  to a logical one and the output  560  to a logical one if the voltage envelope of the signal received from the active signal processing circuit  514  or  530  exceeds the first limit and the second limit. The outputs  558 ,  560  of the signal strength detector  556  are connected to inputs  562 ,  564  of a bias selector  566 .  
         [0130]    The bias selector  566  provides signals that indicate the bias setting for each of the first and second signal processing circuits  514 ,  530 . The bias selector includes the input  562 , the input  564 , an input  565 , an input  567 , an input  569 , an output  568 , an output  570 , an output  572 , an output  574 , an output  576 , an output  578 , and an output  584 . The outputs  568 ,  670 ,  572  of the bias selector  566  are connected to the inputs  506 ,  508 ,  510 , respectively, of the first signal processing circuit  514 . The outputs  574 ,  576 ,  578  of the bias selector  566  are connected to the inputs  522 ,  524 ,  526 , respectively, of the second signal processing circuit  530 , and the output  584  of the bias selector  566  corresponds to input  586  of a timer  588 . The outputs  568 ,  570 ,  572  of the bias selector  566  indicate the bias setting for the first signal processing circuit  514 , and the outputs  574 ,  576 ,  578  of the bias selector  566  indicate the bias setting for the second signal processing circuit  530 . The input  565  indicates when the timer  588  has completed the transition from one of the first and second signal processing circuits  514 ,  530  to the other of the first and second signal processing circuits  514 ,  530 . The inputs  567 ,  569  indicate the current state of the timer  588 .  
         [0131]    The bias selector  566  transmits the bias setting for the active signal processing circuit  514  or  530  to the active signal processing circuit  514  or  530 . If the strength detector  556  indicates that the appropriate bias setting is different than the bias setting of the active signal processing circuit  514  or  530 , the bias selector  566  transmits the appropriate bias setting to the inactive signal processing circuit (i.e., the one of the first and second signal processing circuits  514 ,  430  not having its output  518 ,  534  connected to the system output  594 ). The timer  588  eventually changes the inactive signal processing circuit into the active signal processing circuit, and the active signal processing circuit into the inactive signal processing circuit. Once the timer  588  completes this transition, the bias selector  566  discontinues providing the inactive signal processing circuit with a bias setting.  
         [0132]    The timer  588  provides signals that selectively connect and disconnect the first and second signal processing circuits  514 ,  530  to and from the system output  594  of the signal processing system  500 , and selectively turn the first and second signal processing circuits  514 ,  530  on and off. The timer  588  includes the input  586 , an output  580 , an output  582 , an output  590 , an output  592 , an output  587 , an output  589  and an output  591 . The outputs  580 ,  582  of the timer  588  are connected to the inputs  528 ,  512 , of the first and second signal processing circuits  530 ,  514 , respectively. The outputs  590 ,  592  of the timer  588  are connected to the switch control inputs  538 ,  546 , of the first and second switches  540 ,  548 , respectively. The timer  588  provides signals that cause only one of the outputs  518 ,  534  of one of the first and second signal processing circuits  514 ,  530 , to be connected to the system output  594  of the signal processing system  500  at any one time.  
         [0133]    The timer  588  provides signals to the first and second switches  540 ,  548  and the first and second signal processing circuits  514 ,  530  that allow the system output  594  to switch between output  518 ,  534  of the first signal processing circuit  514  and the second signal processing circuit  530  without causing transients to appear at the system output  594  of the signal processing system  500 . To switch from the output of one signal processing circuit to the output of the other signal processing circuit, the timer  558  provides a signal at the output  580 ,  582  to turn on the first or second signal processing circuit  530 ,  514  selected by the bias selector  566 . If the bias selector  566  selected the first signal processing circuit  514 , and the second signal processing circuit  530  is connected to the system output  594 , the timer  588  turns on the first signal processing circuit  514  by providing first a logical one on its output  582 . If the bias selector  566  selected the signal processing circuit  530 , and the signal processing circuit  514  is connected to the system output  594 , the timer  588  turns on the second signal processing circuit  530  by providing a logical one on the output  580 .  
         [0134]    After the first or second signal processing circuit  514 ,  530  selected by the signal strength detector  588  is turned on, the timer  588  waits a length of time sufficient for transients at the outputs  518 ,  534  of the first and second signal processing circuits  514 ,  530 , to die out. After the length of time elapses, the timer  588  connects the output  518 ,  534  of the first or second signal processing circuit  514 ,  530 , indicated by the bias selector  566 , to the system output  594  of the signal processing system  500 . If the bias selector  566  selected the first signal processing circuit  514 , the timer  588  closes the first switch  540  by providing a logical one on the output  590 , and opens the second switch  548  by providing a logical zero on the output  592 . If the bias selector  566  selected the second signal processing circuit  530 , the timer  588  closes the second switch  548  by providing a logical one on its output  592 , and opens the first switch  540  by providing a logical zero on its output  590 .  
         [0135]    In an alternate exemplary embodiment, more than two signal processor circuits are provided for selective connection between the system input  502  and the system output  594  of the signal processing system  500  with appropriate modifications to the signal strength detector  556 , the bias selector  566 , and the timer  588 .  
         [0136]    In another alternate exemplary embodiment, the first and second signal processing circuits  514 ,  530  are not turned off, but are placed in a standby mode whereby they consume less power than when they are fully on. Placing the first and second signal processing circuits  514 ,  530  in a standby mode reduces the length of time the timer  588  has to wait before the transients at the outputs  518 ,  534 , of the first and second signal processing circuits  514 ,  530  die out, therefore speeding up switching time.  
         [0137]    In an exemplary embodiment, the first signal processing circuit  514  can be the signal processing circuit  1500  illustrated in FIG. 15. The input  504  of the first signal processing circuit  514  becomes an input  1502  of the signal processing circuit  1500 , the input  506  becomes an input  1504 , the input  508  becomes an input  1506 , the input  510  becomes an input  1508 , the input  512  becomes an input  1523 , and the output  518  becomes an output  1520 . The signal processing circuit  1500  includes a dynamic input scaling unit  1518 , a biquad  1526 , and a dynamic output scaling unit  1538 .  
         [0138]    A signal received at the input  1502  of the signal processing circuit  1500  is conveyed to an input  1510  of the dynamic input scaling unit  1518 ; a signal received at the input  1504  is conveyed to an input  1512  of the dynamic scaling unit  1518  and an input  1532  of the dynamic output scaling unit  1538 ; a signal received at the input  1506  is conveyed to an input  1514  of the dynamic input scaling unit  1518  and an input  1534  of the dynamic output scaling unit  1538 ; a signal received at the input  1508  is conveyed to an input  1516  of the dynamic input scaling unit  1518  and an input  1536  of the dynamic output scaling unit  1538 ; and a signal received at the input  1523  is conveyed to an input  1524  of the biquad  1526 . The dynamic input scaling unit  1518  processes the signal received at the input  1510  and provides a signal at an output  1520  of the dynamic input scaling unit  1518  based on the signal received at the input  1510  and the signals received at the inputs  1504 ,  1506 ,  1508 . The output  1520  corresponds to input  1522  of the biquad  1526 .  
         [0139]    The biquad  1526  processes the signal received at its input  1522  and produces a signal at its output  1528  if the signal received at the input  1524  is a logical one. If the signal received at the input  1524  is a logical zero, the biquad  1526  does not produce a signal at the output  1528 . The output  1528  of the biquad  1526  is connected to the input  1530  of the dynamic output scaling unit  1538 .  
         [0140]    The dynamic output scaling unit  1538  processes the signal received at the input  1530  and provides a signal at its output  1540  based on the signal received at the input  1530  and the signals received at inputs  1532 ,  1534 ,  1536 . The output  1540  is connected to the output  1542  of the signal processing circuit  1500 .  
         [0141]    In an exemplary embodiment, the dynamic input scaling unit  1518  can be the dynamic input scaling unit  1700  illustrated in FIG. 17. The input  1512  of the dynamic input scaling unit  1518  corresponds to input  1702  of the dynamic input scaling unit  1700 , the input  1516  corresponds to an input  1708 , the input  1510  corresponds to input  1704 , and the output  1520  becomes an output  1756 . The dynamic input scaling unit  1700  includes a first switch  1714 , a second switch  1734 , a first resistor  1720 , a second resistor  1726 , a first transconductor  1742 , and a second transconductor  1752 .  
         [0142]    A signal received at the input  1702  of the dynamic input scaling unit  1700  is conveyed to an inverted switch control input  1710  of the first switch  1714 , and an input  1732  of the second switch  1734 ; a signal received at the input  1704  is conveyed to one terminal  1718  of the first resistor  1720  and an input  1712  of the first switch  1714 ; and an input  1708  is conveyed to a switch input  1750  of the transconductor  1752 . The first switch  1714  connects its input  1712  to its output  1716  if the signal received at the inverted switch control input  1710  is a logical zero. If the signal at the inverted switch-control input  1710  is a logical one, the first switch  1714  disconnects its input  1712  from its output  1716  resulting in an open circuit. The first resistor  1720  is connected between the input  1712  signal received at the input  1718  of the and the output  1716  of the first switch  1714 . The output  1716  of the first switch  1714  and the other terminated  1722  of the first resistor  1720  are both connected to one terminal  1724  of the second resistor  1726 , a positive input  1738  of the first transconductor  1742 , and a positive input  1746  of the second transconductor  1752 . The first switch  1714  and the first resistor  1720  form one half of a voltage divider, which is used to adapt a filter to be useful over a high effective range.  
         [0143]    The other terminal  1728  of the second resistor  1726  corresponds to input  1730  of the second switch  1734 . The second switch  1734  connects its input  1730  to its output  1736  if the signal received at the switch control input  1732  is a logical one. If the signal at the switch control input  1732  is a logical zero, the second switch  1734  disconnects its input  1730  from its output  1736  resulting in an open circuit. The second switch  1734  and the second resistor  1726  form the other half of the voltage divider used to adapt signal processing circuit  1500  to have a high effective range.  
         [0144]    The first transconductor  1742  processes the difference between the signal received at its positive input  1738  and the signal received at its negative input  1740 , which is connected to ground, and provides a signal at its output  1744 . The signal at the output  1744  of the first transconductor  1742  is equal to the difference in the signal received by the positive input  1738  of the first transconductor  1742  and the signal received by its negative input  1740 , scaled by a transconductance G m  of the first transconductor  1742 . The output  1744  of the first transconductor  1742  corresponds to output  1754  of the second transconductor  1752 , and the output  1756  of the dynamic input scaling unit  1518 . When the first switch  1714  is closed, the switch  1734  is open, and the second transconductor  1752  is off (as a result of a logical zero signal received at its control input  1750 ), the voltage output of the first transconductor  1742  adapts the signal processing circuit  1500  to a medium effective range.  
         [0145]    If a logical one signal is received at the control terminal  1750  of the second transconductor  1752 , it processes the difference between the signal received at its positive input  1746  and the signal received at its negative input  1748 , which is connected to ground, and provides a signal at the output  1754 . If the signal at its control input  1750  is a logical zero, the second transconductor  1752  acts as an open circuit between its input  1746  and its output  1754 . If the signal at the control input  1750  is a logical one, the signal at the output  1754  of the second transconductor  1752  is equal to the difference in the signal received by its positive input  1746  and the signal received by its negative input  1748 , scaled by a transconductance 9G m  of the second transconductor  1752 . The output  1754  of the second transconductor  1752  is connected to the output  1744  of the first transconductor  1742 , and to the output  1756  of the dynamic input scaling unit  1518 . When the second transconductor  1752  is on, i.e. when the signal at its control input  1750  is a logical one, the voltage output of the transconductor  1752  combines with the voltage output of the transconductor  1742  to adapt a signal processing circuit to have a low effective range.  
         [0146]    Referring again to FIG. 15, the biquad  1526  of the signal processing circuit  1500  can be the biquad  1600  illustrated in FIG. 16. Turning to FIG. 16, the biquad  1600  includes a first transconductor  1614 , a second transconductor  1622 , a third transconductor  1630 , a fourth transconductor  1644 , a first capacitor  1606 , and a second capacitor  1636 . The center frequency Wo of the biquad  1600  can be calculated equation (1). The absolute value of the transconductors and capacitors can be scaled by the same factor, i.e. impedance scaling, without affecting the transfer function of the biquad  1600 , since the transfer function depends on the ratios between these values. Impedance scaling does not change the transfer function of the biquad  1600 , however it does change the power dissipation and the noise level of the biquad  1600 .  
         [0147]    A signal received by the input  1602  of the biquad  1600  is conveyed to one terminal  1604  of the capacitor  1606 , a negative input  1610  of the first transconductor  1614 , an output  1616  of the first transconductor  1614 , a positive input  1618  of the second transconductor  1622 , and an output  1632  of the third transconductor  1630 . These connections form a node  1617 . The other terminal  1608  of the first capacitor  1606  is connected to ground. The first capacitor  1606  buffers the first node  1074  by being connected to ground through the capacitor  1606 .  
         [0148]    If its control input  1652  receives a logical one signal, the first transconductor  1614  processes the difference between the signal received at its positive input  1612 , which is connected to ground, and the signal received at its negative input  1610 , and provides a signal at its output  1616 . The signal at the output  1616  is equal to the difference between the signal received by the positive input  1610  and the signal received by the negative input  1612 , scaled by a transconductance G m  of the first transconductor  1614  if the signal received at the control input  1652  is a logical one. If the signal received at the control input  1652  is a logical zero, the output  1616  of the first transconductor  1614  acts as an open circuit. The output  1616  of the transconductor  1614  is connected to one terminal  1604  of the first capacitor  1606 , the negative input  1610  of the first transconductor  1614 , the positive input  1618  of the second transconductor  1622 , and the output  1632  of the third transconductor  1630 . The transconductor  1614  forms a feedback loop at the node  1617 .  
         [0149]    If its control input  1656  receives a logical one signal, the transconductor  1622  processes the difference between the signal received at its positive input  1618  and the signal received at its negative input  1620 , which is connected to ground, and outputs a signal at its output  1624 . The signal at the output  1624  is equal to the difference between the signal received by the positive input  1618  and the signal received by the negative input  1620 , scaled by a transconductance QG m  of the second transconductor  1622  if the signal received at the control input  1656  is a logical one. If the signal received at the input  1656  is a logical zero, the output  1624  of the second transconductor  1622  acts as an open circuit. The output  1624  of the second transconductor  1622  is connected to one terminal second  1634  of the second capacitor  1636 , the negative input  1626  of the third transconductor  1630 , and the positive input  1640  of the fourth transconductor  1644 . These connections form a node  1625 . The other terminal  1638  of the capacitor  1636  is connected to ground so as to buffer node  1625 .  
         [0150]    If its second control input  1654  receives a logical one signal the third transconductor  1630  processes the difference between the signal received at its positive input  1628 , which is connected to ground, and the signal received at its negative input  1626  and outputs a signal at its output  1632 . The signal at the output  1632  is equal to the difference between the signal received by the positive input  1628  and the signal received by the negative input  1626 , scaled by a transconductance QG m  of the third transconductor  1630  if the signal received at the control input  1654  is a logical one. If the signal received at the input  1654  is a logical zero, the output  1632  of the third transcondutor  1630  acts as an open circuit. The output  1632  of the third transconductor  1630  is connected to one terminal  1604  of the capacitor  1606 , the negative input  1610  of the first transconductor  1614 , the output  1616  of the first transconductor  1614 , and the positive input  1618  of the second transconductor  1622 . The second and third transconductors  1622 ,  1630  form a feedback loop at the node  1617 .  
         [0151]    If its control input  1658  receives a logical one signal, the fourth transconductor  1644  processes the difference between the signal received at its positive input  1640  and the signal received at its negative input  1642 , which is connected to ground, and provides a signal at its output  1646 . The signal at the output  1646  is equal to the difference in the signal received by the positive input  1640  and the signal received by the negative input  1642  of the fourth transconductor  1644 , scaled by a transconductance QG m  of the fourth transconductor  1644  if the signal at its control input  1658  is a logical one. If the signal received at the control input  1658  is a logical zero, the output  1646  of the fourth transconductor acts as an open circuit. The output  1646  of the fourth transconductor  1644  corresponds to output  1648  of the biquad  1600 .  
         [0152]    In an exemplary embodiment, a first diode and a second diode are connected to the node  1617 . The cathode of the first diode is connected to the node  1617 , and the anode of the first diode is connected to ground. The anode of the second diode is connected to the node  1617 , and the cathode of the second diode is connected to ground. The first and second diodes serve to limit the voltage swing at node  1617  to approximately ±0.7 v.  
         [0153]    In an exemplary embodiment, a first diode and a second diode are connected to the node  1625 . The cathode of the first diode is connected to the node  1625 , and the anode of the first diode is connected to ground. The anode of the second diode is connected to the node  1625 , and the cathode of the second diode is connected to ground. The first and second diodes serve to limit the voltage swing at node  1625  to approximately ±0.7 v.  
         [0154]    In an alternative exemplary embodiment, the dynamic output scaling unit  1538  can be the dynamic output scaling unit  1800  illustrated in FIG. 18. The input  1530  of the dynamic output scaling unit  1538  corresponds to input  1802  of the dynamic output scaling unit  1800 , the input  1532  corresponds to input  1804 ; the input  1534  corresponds to input  1806 , the input  1536  corresponds to input  1808 , and the output  1540  corresponds to output  1852 . The dynamic output scaling unit  1800  includes a first resistor  1812 , a first switch  1820 , a second resistor  1826 , a second switch  1834 , a third resistor  1840 , and a third switch  1848 .  
         [0155]    A signal received at the input  1802  of the dynamic output scaling unit  1800  is applied to one terminal  1810  of the first resistor  1812 , one terminal  1824  of the second resistor  1826 , and one terminal  1838  of the third resistor  1840 . A signal received at the input  1804  is conveyed to a switch control input  1846  of the third switch  1848 ; a signal received at the input  1806  is conveyed to a switch control input  1832  of the second switch  1834 ; and a signal received at the input  1808  is conveyed to its terminal input  1818  of the first switch  1820 . The first resistor  1812  couples the signal applied to its terminal  1810  to input  1816  of the first switch  1820 . The first switch  1820  connects its input  1816  to its output  1822  if the signal received at the switch control input  1818  is a logical one. If the signal at the switch control input  1818  is a logical zero, the first switch  1820  disconnects its input  1816  from its output  1822  resulting in an open circuit between the input and its output. The output  1822  of the first switch  1820  is connected to ground. The resistor  1812  and the switch  1820  form an effective amplifier which provides a relatively small gain for the signal received at the input  1802 , which is used to adapt the signal processor circuit  1500  to have a low effective range.  
         [0156]    The second resistor  1826  couples the signal applied to its terminal  1824  to an input  1830  of the second switch  1834 . The second switch  1834  connects its input  1830  to its output  1836  if the signal received at the switch control input  1832  is a logical one. If the signal at the switch control input  1832  is a logical zero, the switch  1834  disconnects its input  1830  from its output  1836  resulting in an open circuit between the input and the output. The output  1836  of the second switch  1834  is connected to ground. The resistor  1826  and the switch  1834  form an effective amplifier which provides a medium gain for the signal received at the input  1802 , which is used to adapt the signal processing circuit  1500  to have a medium effective range.  
         [0157]    The third resistor  1840  couples the signal applied to its terminal  1838  to the input  1844  of the third switch  1848 . The switch  1848  connects its input  1844  to its output  1850  if the signal received at the switch control input  1846  is a logical one. If the signal at the switch control input  1846  is a logical zero, the third switch  1848  disconnects its input  1844  output  1850  resulting in an open circuit between the input and the output. The output  1850  of the third switch  1848  is connected to ground. The resistor  1840  and the switch  1848  form an effective amplifier which provides a relatively large gain for the signal received at the input  1802 , which is used to adapt the signal processing circuit  1500  to have a high effective range.  
         [0158]    In an exemplary embodiment, the signal strength detector  556  of the signal processing circuit  1500  of FIG. 15 is described in FIG. 21 as signal strength detector  2100 . The signal strength detector  2100  senses the voltage envelope of the selected input signal of the inputs  552 ,  554  (shown in FIG. 5), and selects an appropriate signal processing circuit  514 ,  530  based on a first and a second threshold limit. An input signal is selected when a first switch  2106  or a second switch  2114  is closed. The first threshold limit represents a point at which the signal received from the active signal processing circuit  514  or  530  is near its minimum tolerable signal to noise ratio. The second threshold limit represents a point at which the active signal processing circuit  514  or  530  is near saturation. The signal strength detector  2100  includes the first switch  2106 , the second switch  2114 , a peak detector  2120 , a first threshold detector  2126 , and a second threshold detector  2134 . The peak detector  2120 , the first threshold detector  2126 , and the second threshold detector  2134  are described in more detail above in relation to FIG. 11.  
         [0159]    A signal received at the input  554  is conveyed to the input  2102  of the first switch  2106 ; a signal received at the input  552  is conveyed to an input  2110  of the second switch  2114 ; and a signal received at the input  593  is conveyed to a switch control input  2104  of the first switch  2106  and an inverted switch control input  2112  of the second switch  2114 . If the signal received at the input  593  is a logical one, the first switch  2106  closes connecting the signal received at its input  2102  to its output  2108  and the second switch  2114  opens. The output  2108  of the first switch  2106  is connected to the input  2118  of a peak detector  2120 . If the signal received at the input  593  is a logical zero, the second switch  2114  closes connecting the signal received at its input  2110  and to its  2116 , and the first switch  2106  closes. The output of the second switch  2114  is connected to the input  2118  of the peak detector  2120 .  
         [0160]    The peak detector  2120  processes the signal received at its input  2118  and provides a signal at its output  2122 . The signal output at the output  2122  is conveyed to the input  2124  of a first threshold detector  2126  and the input  2132  of a second threshold detector  2134 . The first threshold detector  2126  provides a logical one signal at its output  2128  if the signal at its input  2124  exceeds the first threshold limit, and provides a logical zero signal on its output  2128  if the signal at its input  2124  does not exceed the first threshold limit. The output  2128  of the first threshold detector  2126  is connected to the output  558  of the signal strength detector  2100 . The second threshold detector  2134  provides a logical one signal on its output  2136  if the signal at its input  2132  exceeds the second threshold limit, and provides a logical zero signal on its output  2136  if the signal at its input  2132  does not exceed the second threshold limit. The output  2136  of the second threshold detector  2134  is connected to the output  560  of the strength detector  2100 .  
         [0161]    The first threshold detector  2126 , which is similar to the first threshold detector  1175  shown in FIG. 11, is configured to detect the first limit. Referring to FIG. 11, the current source  1170  of the threshold detector  2126  produces a reference current that represents the first limit. The reference current provided by its current source  1170  of the first threshold detector  2126  can be 11 micro-amperes. The second threshold detector  2136 , which is also similar to the first threshold detector  1175  shown in FIG. 11, is configured to detect the second limit. The current source  1170  of the threshold detector  2134  produces a reference current that represents the second limit. The reference current provided by the current source  1170  of the second threshold detector  2134  can be 110 micro-amperes.  
         [0162]    In an exemplary embodiment, the bias selector  566  (shown in FIG. 5) can be the bias selector  1900  as described in FIGS. 19 and 20. The bias selector  1900  indicates the bias setting for the first and second signal processing circuits  514 ,  530 , and when the timer  588  (shown in FIG. 5) should switch the active signal processing circuit from one signal processing circuit to the other signal processing circuit.  
         [0163]    Referring to FIG. 19, signals received at the inputs  562 ,  564  are conveyed to an array of AND gates, and a signal received at the input  1906  is conveyed to the clock inputs  1944 ,  1952  and  1960  of positive edge triggered D-type flip flops  1946 ,  1954  and  1962 , respectively. The data output  1948  of the positive edge triggered D-type flip flop  1946  is connected to the output  584  of the bias selector  566 .  
         [0164]    A five input AND gate  1908  processes the inverse of a signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the inverse of a signal from the data output  1956  of the positive edge triggered D-type flip flop  1954 , the inverse of a signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , the inverse of a signal by the input  562 , and the inverse of a signal received by the input  564 , and produces an output which is provided to a respective input of a four input OR gate  1920 . A five input AND gate  1910  processes the inverse of the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the inverse of the signal from the data output  1956  of the positive edge triggered D-type flip flop  1954 , the signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , the signal received by the input  562 , and the signal by the input  564 , and produces an output which is provided to a respective input of the four input OR gate  1920 . A five input AND gate  1914  processes the inverse of the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the signal from the data output  1956  of the positive edge triggered D-type flip flop  1954 , the inverse of the signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , the signal received by the input  562 , and the signal received by the input  564 , and produces an output which is provided to a respective input of the four input OR gate  1920 . A five input AND gate  1916  processes the inverse of the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the inverse of the signal from the data output  1956  of the positive edge triggered D-type flip flop  1954 , the signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , the inverse of the signal received by the input  562 , and the inverse of the signal by the input  564 , and produces an output which is provided to a respective input of the four input OR gate  1920 . The four input OR gate  1920  processes the signals received at its inputs and produces an output which is provided to the data input  1942  of the positive edge triggered D-type flip flop  1946 .  
         [0165]    A five input AND gate  1924  processes the inverse of the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the inverse of the signal from the data output  1956  of the positive edge triggered D-type flip flop  1954 , the signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , the signal received by the input  562 , and the signal received by the input  564 , and produces an output which is provided to a respective input of a two input OR gate  1930 . A five input AND gate  1926  processes the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the inverse of the signal from the data output  1956  of the positive edge triggered D-type flip flop  1954 , the inverse of the signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , the inverse of the signal by the input  562  and the inverse of the signal received by the input  564 , and produces an output which is provided to a respective input of the two input OR gate  1930 . The two input OR gate  1930  processes the signals received at its inputs and produces an output which is provided to the data input  1950  of the positive edge triggered D-type flip flop  1954 .  
         [0166]    A five input AND gate  1932  processes the inverse of the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the inverse of the signal from the data output  1956  of the positive edge triggered D-type flip flop  1954 , the signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , the inverse of the signal by the input  562 , and the inverse of the signal by the input  564 , and produces an output which is provided to a respective input of a three input OR gate  1940 . A five input AND gate  1934  processes the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the signal from the data output  1956  of the positive edge triggered D-type flip flop  1954 , the inverse of the signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , the inverse of the signal received by the input  562 , and the inverse of the signal received by the input  564 , and produces an output which is provided to a respective input of the three input OR gate  1940 . A five input AND gate  1936  processes the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the inverse of the signal received from the data output  1956  of the positive edge triggered D-type flip flop  1954 , the signal received from the data output  1964  of the positive edge triggered D-type flip flop  1962 , the signal received by the input  562  and the signal received by the input  564 , and produces an output which is provided to a respective input of the three input OR gate  1940 . The three input OR gate  1940  processes the signals received at its inputs and produces an output which is provided to the data input  1958  of the positive edge triggered D-type flip flop  1960 .  
         [0167]    A three input AND gate  1966  processes the inverse of the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the inverse of the signal from the data output  1956  of the positive edge triggered D-type flip flop  1954 , and the inverse of the signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , and produces an output which is provided to one input of a two input OR gate  1970 . A three input AND gate  1968  processes the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the signal from the data output  1956  of the positive edge triggered D-type flip flop  1954 , and the inverse of the signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , and produces an output which is provided to the other input of the two input OR gate  1970 . The two input OR gate  1970  processes the signals received at its inputs and produces an output signal at its output  1972  which is provided to the data input  2002  of a positive edge triggered D-type flip flop  2006 , shown in FIG. 20.  
         [0168]    A three input AND gate  1974  processes the inverse of the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the inverse of the signal from the data output  1956  of the positive edge triggered D-type flip flop  1954  and the signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , and produces an output which is provided to one input of a two input OR gate  1978 . A three input AND gate  1976  processes the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the inverse of the signal from the data output  1956  of the positive edge triggered D-type flip flop  1954 , and the inverse of the signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , and produces an output which is provided to the other input of the two input OR gate  1978 . The two input OR gate  1978  processes the signals received at its inputs and produces an output signal at its output  1980  which is provided to the data input  2010  of a positive edge triggered D-type flip flop  2014 , shown in FIG. 20.  
         [0169]    A three input AND gate  1982  processes the inverse of the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the signal received from the data output  1956  of the positive edge triggered D-type flip flop  1954 , and the inverse of the signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , and produces an output which is provided to one input of a two input OR gate  1986 . A three input AND gate  1984  processes the signal from the data output  1948  of the positive edge triggered D-type flip flop  1946 , the inverse of the signal from the data output  1956  of the positive edge triggered D-type flip flop  1954  and the signal from the data output  1964  of the positive edge triggered D-type flip flop  1962 , and produces an output which is provided to the other input of the two input OR gate  1986 . The two input OR gate  1986  processes the signals received at its inputs and produces an output signal at its output  1988  which is provided to the data input  2018  of a positive edge triggered D-type flip flop  2022 , shown in FIG. 20.  
         [0170]    Referring now to FIG. 20, a signal received at an input  565  is conveyed to the clock input  2004  of the positive edge triggered D-type flip flop  2006 , the clock input  2012  of the positive edge triggered D-type flip flop  2014 , and a clock input  2020  of the positive edge triggered D-type flip flop  2006 .  
         [0171]    A two input AND gate  2026  processes the signal from the data output  2008  of the positive edge triggered D-type flip flop  2006 , and the inverse of the signal received by the input  569  of the bias selector  566 , and produces an output which is provided to one input of a two input OR gate  2030 . A three input AND gate  2028  processes the signal from the output  1972  of the two input OR gate  1970  (shown in FIG. 19), the inverse of the signal received by the input  569  of the bias selector  566 , and the signal received by the input  567  of the bias selector  566 , and produces an output which is provided to the other input of the two input OR gate  2030 . The two input OR gate  2030  processes the signals received at its inputs and produces an output signal at the output  572  of the bias selector  566 .  
         [0172]    A two input AND gate  2034  processes the signal from the data output  2016  of the positive edge triggered D-type flip flop  2014 , and the inverse of the signal received by the input  569  of the bias selector  566 , and produces an output which is provided to one input of a two input OR gate  2038 . A three input AND gate  2036  processes the signal received from the output  1980  of the two input OR gate  1978  (shown in FIG. 19), the inverse of the signal received by the input  569  of the bias selector  566 , and the signal received by the input  567  of the bias selector  566 , and produces an output which is provided to the other input of the two input OR gate  2038 . The two input OR gate  2038  processes the signals received at its inputs and produces an output signal at the output  570  of the bias selector  566 .  
         [0173]    A two input AND gate  2042  processes the signal from the data output  2024  of the positive edge triggered D-type flip flop  2022 , and the inverse of the signal received by the input  569  of the bias selector  566 , and produces an output which is provided to one input of a two input OR gate  2046 . A three input AND gate  2044  processes the signal from the output  1988  of the two input OR gate  1986 , the inverse of the signal received by the input  569  of the bias selector  566 , and the signal received by the input  567  of the bias selector  566 , and produces an output which is provided to the other input of the two input OR gate  2046 . The two input OR gate  2046  processes the signals received at its inputs and produces an output signal at the output  568  of the bias selector  566 .  
         [0174]    A three input AND gate  2050  processes the signal from the output  1972  of the two input OR gate  1970 , the signal received by the input  569  of the bias selector  566 , and the inverse of the signal received by the input  567  of the bias selector  566 , and produces an output which is provided to one input of the two input OR gate  2054 . A two input AND gate  2052  processes the signal from the data output  2008  of the positive edge triggered D-type flip flop  2006 , and the signal received by the input  569  of the bias selector  566 , and produces an output which is provided to the other input of the two input OR gate  2054 . The two input OR gate  2054  processes the signals received at its inputs and produces an output signal at the output  578  of the bias selector  566 .  
         [0175]    A three input AND gate  2058  processes the signal from the output  1980  of the two input OR gate  1982 , the signal received by the input  569  of the bias selector  566  and the inverse of the signal received by the input  567  of the bias selector  566 , and produces an output which is provided to one input of the two input OR gate  2062 . A two input AND gate  2060  processes the signal from the data output  2016  of the positive edge triggered D-type flip flop  2014  and the signal received by the input  569  of the bias selector  566 , and produces an output which is provided to the other input of the two input OR gate  2062 . The two input OR gate  2062  processes the signals received at its inputs and produces an output signal at the output  576  of the bias selector  566 .  
         [0176]    A three input AND gate  2066  processes the signal from the output  1988  of the two input OR gate  1986 , the signal received by the input  569  of the bias selector  566  and the inverse of the signal received by the input  567  of the bias selector  566 , and produces an output which is provided to one input of the two input OR gate  2070 . A two input AND gate  2068  processes the signal from the data output  2024  of the positive edge triggered D-type flip flop  2022  and the signal received by the input  569  of the bias selector  566 , and produces an output which is provided to the other input of the two input OR gate  2070 . The two input OR gate  2070  processes the signals received at its inputs and produces an output signal at the output  574  of the bias selector  566 .  
         [0177]    In an exemplary embodiment, the timer  588  can be the timer  1300  illustrated in FIG. 13. The input  586  of the timer  588  corresponds to the input  1302  of the timer  1300 , and the outputs  580 ,  582 ,  590 ,  592  of the timer  588  correspond to the outputs  1319 ,  1309 ,  1394 ,  1399 , respectively, of the timer  1300 . The timer  1300  provides outputs  1309 ,  1319 ,  1394  and  1399  that selectively connect and disconnect the first and second signal processing circuits  514 ,  530  to and from the input  502  and the output  594  of the signal processing system  500 , and selectively turn the first and second signal processing circuits  514 ,  530  on and off. The timer  1300  includes a first three input AND gate  1312 , a second three input AND gate  1322 , a third three input AND gate  1332 , a fourth three input AND gate  1342 , a first three input OR gate  1350 , a second three input OR gate  1358 , a third three input OR gate  1397 , a two input NAND gate  1392 , a two input NOR gate  1305 , a two input AND gate  1315 , a first Dtype flip-flop  1366 , a second D-type flip-flop  1374 , an XOR gate  1382 , and an n-bit overflow counter  1388 . The timer  1300  is provided with two inputs: a signal strength detector input  1302  and a clock input  1304 .  
         [0178]    The first three input AND gate  1312 , the second three input AND gate  1322 , and the first three input OR gate  1350  combine to produce the most significant bit for the next state of the state machine. The first three input AND gate  1312  includes an inverting input  1306 , an input  1308 , an input  1310 , and an output  1314 . The inverting input  1306  is connected to an input  1316  of the second three input AND gate  1322 , an inverting input  1326  of the third three input AND gate  1332 , an inverting input  1336  of the fourth three input AND gate  1342 , the data output  1368  of the first D-type flip-flop  1366 , the input  1378  of the two input XOR gate  1382 , the input  1390  of the two input NAND gate  1392 , the input  1301  of the two input NOR gate  1305 , the input  1311  of the two input AND gate  1315 , and the input  1395  of the third three input OR gate  1397  are each connected to the output  589  of the timer  588 . The input  1308  of the first three input AND gate  1312 , the input  1318  of the second three input AND gate  1322 , the inverting input  1328  of the third three input AND gate  1332 , the input  1338  of the fourth three input AND gate  1342 , the data output  1376  of the second D-type flip-flop  1374 , the input  1380  of the two input XOR gate  1382 , the input  1391  of the two input NAND gate  1392 , the input  1313  of the two input AND gate  1315 , the input  1303  of the two input NOR gate  1305 , and the input  1396  of the third three input OR gate  1397  are each connected to the output  587  of the timer  588 . The input  1310  of the first three input AND gate  1312 , the input  1340  of the fourth three input AND gate  1342 , and the counter overflow output  1389  of the n-bit overflow counter  1388 , are each connected to the output  591  of the timer  588 . The input  1320  of the third three input AND gate  1322  and the inverting input  1330  of the fourth three input AND gate  1332  are connected to the input  1302  of the timer circuit  1300 . The clock input  1361  of the first negative edge triggered D-type flip-flop  1366 , the clock input  132  of the second negative edge triggered D-type flip-flop  1374  and the clock input  1387  of the n-bit overflow counter  1388  are each connected to the clock input  1304  of the timer  1300 .  
         [0179]    The first three input OR gate  1350  includes the input  1346 , the input  1348  and an output  1352 . The input  1346  is connected to the output  1314  of the first three input AND gate  1312 . The input  1348  is connected to the output  1324  of the second three input AND gate  1322 . And the output  1352  of the first three input OR gate  1350  is connected to a data input  1362  of the first D-type flip-flop  1366 .  
         [0180]    The third three input AND gate  1332 , the fourth three input AND gate  1342 , and the second three input OR gate  1358  combine to produce the least significant bit for the next state of the state machine.  
         [0181]    The second three input OR gate  1358  includes the input  1354 , the input  1356  and the output  1360 . The input  1354  is connected to the output  1334  of the third three input AND gate  1332 . The input  1356  is connected to the output  1344  of the fourth three input AND gate  1342 . And the output  1360  of the second three input OR gate  1358  is connected to the data input  1370  of the second D-type flip-flop  1374 .  
         [0182]    The first D-type flip-flop  1366  holds the most significant bit of the current state of the timer  1300  until the next negative edge of the clock signal received at the clock input  1304  of the timer  1300 . The second D-type flip-flop  1374  holds the least significant bit of the current state of the timer  1300  until the next negative edge of the clock signal received at the clock input  1304  of the timer  1300 . The two input XOR gate  1382  produces the signal that enables and resets the n-bit overflow counter  1388 . The output  1384  of the two input XOR gate  1382  is connected to the enable/reset enable/reset input  1386  of the n-bit overflow counter  1388 .  
         [0183]    The n-bit overflow counter  1388  provides a signal that indicates when a given period of time has elapsed. The period of time is adjustable within the n-bit counter  1388 , by configuring the reset conditions of the n-bit counter  1388  such that the period of time can be altered. The n-bit overflow counter  1388  includes the enable/reset input  1386 , the clock input  1387 , and the counter overflow output  1389 . If the enable/reset input  1386  is a logical zero, the n-bit overflow counter  1388  is reset to zero. If the enable/reset input  1386  is a logical one, the n-bit overflow counter  1388  begins to count by increments of one at every falling edge of the clock signal received at the clock input  1387 . The counter overflow output  1389  outputs a logical zero after the n-bit overflow counter  1388  is reset, and continues to output a logical zero until the n-bit overflow counter  1388  overflows. After the n-bit overflow counter  1388  overflows, the counter overflow output  1389  outputs a logical one until the n-bit overflow counter  1388  is reset. The n-bit overflow counter  1388  can be configured or the clock rate can be adjusted to allow for enough time from reset to overflow for the transients in the outputs  518 ,  534  of the signal processing circuits  514 ,  530  to die out.  
         [0184]    The two input NAND gate  1392  produces a signal at its output  1393  that indicates when a signal processing circuit, having a higher effective range, should be turned on and connected to the input of the signal processing system. The two input NAND gate  1392  includes the input  1390 , the input  1391 , and an output  1393 . The input  1390  of the two input NAND gate  1392  is connected to the inverting input  1306  of the first three input AND gate  1312 , the input  1316  of the second three input AND gate  1322 , the inverting input  1326  of the third three input AND gate  1332 , the inverting input  1336  of the fourth three input AND gate  1342 , the output  1368  of the first D-type flip-flop  1366 , the output  589  of the timer  588 , the input  1378  of the two input XOR gate  1382 , the input  1305  of the two input NOR gate  1305 , the input  1311  of the two input AND gate  1315 , and the input  1395  of the third three input OR gate  1397 . The input  1391  of the two input NAND gate  1392  is connected to the input  1308  of the first three input AND gate  1312 , the input  1318  of the second three input AND gate  1322 , the inverting input  1328  of the third three input AND gate  1332 , the input  1338  of the fourth three input AND gate  1342 , the output  1376  of the second Dtype flip-flop  1374 , the output  587  of the timer  588 , the input  1380  of the two input XOR gate  1382 , the input  1313  of the two input AND gate  1315 , the input  1303  of the two input NOR gate  1305 , and an input  1396  of the third three input OR gate  1397 . The output  1393  of the two input NAND gate  1392  is connected to the output  1394  of the timer  1300 .  
         [0185]    The third three input OR gate  1397  produces a signal that indicates when a signal processing circuit, having a lower effective range, should be turned on and connected to the input of the signal processing system. The two input OR gate  1397  includes the input  1395 , the input  1396 , and an output  1398 . The input  1395  of the third three input OR gate  1397  is connected to the inverting input  1306  of the first three input AND gate  1312 , the input  1316  of the second three input AND gate  1322 , the inverting input  1326  of the third three input AND gate  1332 , the inverting input  1336  of the fourth three input AND gate  1342 , the output  1368  of the first D-type flip-flop  1366 , the output  589  of the timer  588 , the input  1378  of the two input XOR gate  1382 , the input  1301  of the two input NOR gate  1305 , the input  1311  of the two input AND gate  1315 , and the input  1390  of the two input NAND gate  1392 . The input  1395  of the third three input OR gate  1397  is connected to the input  1308  of the first three input AND gate  1312 , the input  1318  of the second three input AND gate  1322 , the inverting input  1328  of the third three input AND gate  1332 , the input  1338  of the fourth three input AND gate  1342 , the output  1376  of the second D-type flip-flop  1374 , the output  587  of the timer  588 , the input  1380  of the two input XOR gate  1382 , the input  1303  of the two input NOR gate  1305 , the input  1311  of the two input AND gate  1315 , and the input  1391  of the two input NAND gate  1392 . The output  1398  of the third three input OR gate  1397  is connected to the output  1399  of the timer  1300 .  
         [0186]    The two input NOR gate  1305  produces a signal that indicates when a signal processing circuit, having a higher effective range, should be connected to the output of a signal processing system. The two input NOR gate  1305  includes the input  1301 , the input  1303 , and an output  1307 . The input  1301  of the two input NOR gate  1305  is connected to the inverting input  1306  of the first three input AND gate  1312 , the input  1316  of the second three input AND gate  1322 , the inverting input  1326  of the third three input AND gate  1332 , the inverting input  1336  of the fourth three input AND gate  1342 , the output  1368  of the first D-type flip-flop  1366 , the output  589  of the timer  588 , the input  1378  of the two input XOR gate  1382 , the input  1390  of the two input NAND gate  1392 , the input  1311  of the two input AND gate  1315 , and the input  1395  of the third three input OR gate  1397 . The input  1303  of the two input NOR gate  1305  is connected to the input  1308  of the first three input AND gate  1312 , the input  1318  of the second three input AND gate  1322 , the inverting input  1328  of the third three input AND gate  1332 , the input  1338  of the fourth three input AND gate  1342 , the output  1376  of the second D-type flip-flop  1374 , the output  587  of the timer  588 , the input  1380  of the two input XOR gate  1382 , the input  1391  of the two input NAND gate  1392 , the input  1313  of the two input AND gate  1315 , and the input  1396  of the third three input OR gate  1397 . The output  1307  of the two input NOR gate  1305  is connected to the output  1309  of the timer  1300 .  
         [0187]    The two input AND gate  1315  produces a signal that indicates when a signal processing circuit, having a lower effective range, should be connected to the output of a signal processing system. The two input AND gate  1315  includes the input  1311 , the input  1313 , and an output  1317 . The input  1311  of the two input AND gate  1315  is connected to the inverting input  1306  of the first three input AND gate  1312 , the input  1316  of the second three input AND gate  1322 , the inverting input  1326  of the third three input AND gate  1332 , the inverting input  1336  of the fourth three input AND gate  1342 , the output  1368  of the first D-type flip-flop  1366 , the output  589  of the timer  588 , the input  1378  of the two input XOR gate  1382 , the input  1390  of the two input NAND gate  1392 , the input  1301  of the two input NOR gate  1305 , and the input  1395  of the third three input OR gate  1397 . The input  1313  of the two input AND gate  1315  is connected to the input  1308  of the first three input AND gate  1312 , the input  1318  of the second three input AND gate  1322 , the inverting input  1328  of the third three input AND gate  1332 , the input  1338  of the fourth three input AND gate  1342 , the output  1376  of the second D-type flip-flop  1374 , the output  587  of the timer  588 , the input  1380  of the two input XOR gate  1382 , the input  1391  of the two input NAND gate  1392 , the input  1303  of the two input NOR gate  1305 , and the input  1396  of the third three input OR gate  1397 . The output  1317  of the two input AND gate  1315  is connected to the output  1319  of the timer  1300 .  
         [0188]    Referring to FIG. 5( b ), there is shown a signal processing system  599  according to another exemplary embodiment of the present invention. Unlike the signal processing system  500 , the signal processing system  599  includes the input switch  505 , the input switch  513 , and the outputs  580 ,  582  of the timer  588  are not only connected to the power control inputs  528 ,  512  of the signal processing circuits  530 ,  514 , respectively, but also to switch control inputs  519 ,  517  of the input switches  513 ,  505 , respectively. A signal received by the input  502  is connected to a signal input  501  of the input switch  505  and a signal input  509  of the input switch  513 . The input switch  505  includes the signal input  501 , a grounded input  503 , a switch output  507 , and a switch control input  517 . The input switch  505  connects the signal input  501  to the switch output  507  if the signal received at the switch control input  517  is a logical one, and connects the switch output  507  to the grounded input  503  if the signal received at the switch control input  517  is a logical zero. The switch  513  includes the signal input  509 , a grounded input  511 , a switch output  515 , and a switch control input  519 . The switch  513  connects the signal input  509  to the switch output  515  if the signal received at the switch control input  519  is a logical one, and connects the switch output  515  to the grounded input  511  if the signal received at the switch control input  519  is a logical zero.  
         [0189]    [0189]FIG. 6 illustrates a further exemplary embodiment of a signal processing system  600  in accordance with the present invention. Whenever a large out-band component is present, relative to the in-band signal, in the signal at the input  602  of the signal processing system  600 , a filter with a large signal-to-noise ratio (hereinafter “SNR”) is needed to ensure that after the out-band component is filtered out of the signal the in-band component of the signal is still above the minimum tolerable signal to noise ratio of the filter. However, a filter with a large SNR consumes a relatively large amount of power during operation. When no large out-band component is present in the signal at the input of the signal processing system  600 , a filter with a lower SNR can be used, which consumes a smaller amount of power.  
         [0190]    A signal received at the input  602  of the signal processing system  600  corresponds to input  601  of a signal processing circuit  604 , and an input  603  of a signal processing circuit  606 . The signal processing circuit  604  processes the signal received at the input  602  and outputs a processed signal at the output  607 . The signal processing circuit  604  can be turned on and off by applying an appropriate signal to a power control input  615 . If the signal received at the power input  615  is a logical one, the signal processing circuit  604  is turned on. Conversely, if the signal received at the power input  615  is a logical zero, the signal processing circuit  604  is turned off. The signal processing circuit  604  can process signals with large out-band components because the signal processing circuit  604  has a high SNR. The signal processing circuit  604  therefore introduces low amounts of noise to the processed signal. The output  607  of the signal processing circuit  604  corresponds to input  619  of a switch  612  and an input  641  of the signal strength detector  608 . The switch includes the input  619 , a switch control input  627 , and a switch output  623 . The switch output  623  of the switch  612  is connected to the output  616  of the signal processing system  600 , and an output  625  of a switch  614 .  
         [0191]    The signal processing circuit  606  processes the signal received at the input  603  and outputs a processed signal at the output  609 . The signal processing circuit  606  can be turned on and off by applying an appropriate signal to a power control input  617 . If the signal received at the power control input  617  is a logical one, the signal processing circuit  606  is turned on. Conversely, if the signal received at the power control input  617  is a logical zero signal, the signal processing circuit  606  is turned off. The signal processing circuit  606  has a lower SNR than the signal processing circuit  604 , and therefore introduces higher amounts of noise to the processed signal. The output  609  of the signal processing circuit  606  corresponds to input  621  of a switch  614  and an input  643  of the signal strength detector  608 . The switch  614  includes the input  621 , a switch control input  629 , and the switch output  625 . The switch output  625  of the switch  614  is connected to the output  616  of the signal processing system  600 , and the output  623  of the switch  612 .  
         [0192]    The signal strength detector  608  selects the filter bank that is the most suitable from the standpoint of SNR for processing the signal received by the input  602  of the signal processing system  600 . The inputs  641 ,  643  of the signal strength detector  608  are connected to the outputs  607 ,  609  of the signal processing circuits  604 ,  606 , respectively. The signal strength detector  608  can detect the voltage envelope of the signal at the input  641  of the strength detector  608  and the voltage envelope of the signal at the input  643  of the strength detector  608 . A low-pass-filtered rectifier, well-known for use in many other applications, is one example of a circuit which can be used as an envelope detector. The signal strength detector  608  determines if the voltage envelope of the signal received at the input  641  exceeds a first limit, which represents a point near the minimum tolerable signal to noise ratio of the signal processing circuit  606 , or if the voltage envelope of the signal received at the input  643  exceeds a second limit, which represents a point near the saturation point of the signal processing circuit  604 . If the voltage envelope of the signal at the input  641  exceeds the first limit, or the voltage envdlope of the signal at the input  643  exceeds the second limit, the strength detector  608  provides a logical one on its output  611 . If the voltage envelope of the signal at the input  641  does not exceed the first limit, and the voltage envelope of the signal at the input  643  does not exceed the second limit, the strength detector  608  transmits a logical one on its output  611 .  
         [0193]    The timer  610  provides signals that selectively connect and disconnect the signal processing circuits  604 ,  606  to and from the output  616  of the signal processing system  600 , and selectively turn the signal processing circuits  604 ,  606  on and off. The timer  610  includes the input  639 , a first power control first power control output  631 , an second power control output  633 , an first switch control output  635 , and an second switch control output  637 . The outputs  631 ,  633  of the timer  610  are connected to the power control inputs  615 ,  617  of the first and second signal processing circuits  604 ,  606 , respectively. The first and second switch control outputs  635 ,  637  of the timer  610  are connected to the switch control inputs  627 ,  629  of the switches  627 ,  629 , respectively. The timer  610  provides signals that cause only one of the outputs  607 ,  609  of one of the signal processing circuits  604 ,  606  to be connected to the output  616  of the signal processing system  600  at any one time.  
         [0194]    The timer  610  provides signals to the switches  612 ,  614  and the signal processing circuits  604 ,  606  that allow the signal processing system  600  to switch between the signal processing circuit  604  and the signal processing circuit  606  without causing transients to appear at the output  616  of the signal processing system  600 . To switch from one signal processing circuit to the other signal processing circuit, the timer  610  provides respective signals at the power control outputs  631 ,  633  to turn on the signal processing circuit  604 ,  606  selected by the signal strength detector  608  and to turn off the signal processing circuit  604 ,  606  not selected by the signal strength detector  608 . If the strength detector  608  selected the signal processing circuit  604 , and the signal processing circuit  606  is connected to the output  616 , the timer  610  turns on the signal processing circuit  604  by providing a logical one on the first power control output  631 . If the strength detector  608  selected the signal processing circuit  606 , and the signal processing circuit  604  is connected to the output  616 , the timer  610  turns on the signal processing circuit  606  by providing a logical one on the second power control output  633 .  
         [0195]    After the signal processing circuit  604 ,  606  selected by the signal strength detector  608  is turned on, the timer  610  waits a length of time sufficient for transients at the output  607 ,  609  of the selected signal processing circuits  604 ,  606 , to die out. After the length of time elapses, the timer  610  connects the output  607 ,  609  of the selected signal processing circuit  604 ,  606 , indicated by the strength detector  608  to the output  616  of the signal processing system  600 . If the strength detector  608  selected the signal processing circuit  606 , the timer  610  closes the switch  614  by providing a logical one on the switch control second switch control output  637 , and opens the switch  612  by providing a logical zero on the switch control first switch control output  635 . After the signal processing circuit  614  is disconnected, the timer  610  provides a logical zero on its power control first power control output  631  to turn the disconnected circuit off. If the strength detector  608  selected the signal processing circuit  604 , the timer  610  closes the switch  612  by providing a logical one on the switch control first switch control output  635 , and opens the switch  614  by providing a logical zero on the switch control second switch control output  637 .  
         [0196]    In a further exemplary embodiment, the signal processing circuit  606 , shown in FIG. 6, can be a sixth order bandpass Chebychev filter  1400 , shown in FIG. 14( a ), with a ripple of 0.25 dB, a bandwidth of 0.5 MHz. The sixth order bandpass Chebychev filter  1400  can have a center frequency of 1.25 MHz. The sixth order bandpass Chebychev filter  1400  is constructed by connecting three on-off Tow-Thomas biquads together in series. An on-off Tow-Thomas biquad is constructed in the same manner as the standard Tow-Thomas biquad  800 , shown in FIG. 8, with the exception that the transconductors of the on-off Tow-Thomas biquad are capable of being turned on and off, as described below with reference to FIG. 22.  
         [0197]    Referring to FIG. 14( a ), a signal received by the input  1402  of the sixth order bandpass Chebychev filter  1400  is conveyed to an input  1404  of a first on-off Tow-Thomas biquad  1406 . Assuming that it is turned on, the on-off Tow-Thomas biquad  1406  processes the signal received at the input  1404  and provides a signal at its output  1408 . The first on-off Tow-Thomas biquad  1406  that is turned on advantageously has a transconductance G in  for a transconductor  808  of 771 micro-amperes per volt, a transconductance G m  for a transconductor  824  of 185 micro-amperes per volt, a transconductance QG m  for transconductors  834  and  844  of 591 micro-amperes per volt, and a capacitance for capacitors  816 ,  854  of 77 picofarads. The output  1408  of the first on-off Tow-Thomas biquad  1406  is connected to the input  1410  of a second on-off Tow-Thomas biquad  1412 .  
         [0198]    Assuming that it is turned on, the second on-off Tow-Thomas biquad  1412  processes the signal received at the input  1410  and provides a signal at an output  1414 . The second on-off Tow-Thomas biquad  1412  that is turned on advantageously has a transconductance G in  for the transconductor  808  of 2312 micro-amperes per volt, a transconductance G m  for the transconductor  824  of 185 micro-amperes per volt, a transconductance QG m  for the transconductors  834  and  844  of 1210 micro-amperes per volt, and a capacitance for the capacitors  816 ,  854  of 196 picofarads. The output  1414  of the second on-off Tow-Thomas biquad  1412  corresponds to input  1416  of a third on-off Tow-Thomas biquad  1418 .  
         [0199]    Assuming that it is turned on, the third on-off Tow-Thomas biquad  1418  processes the signal received at the input  1416  and provides a signal at an output  1420 . The third on-off Tow-Thomas biquad  1418  that is turned on advantageously has a transconductance G in  for the transconductor  808  of 971 micro-amperes per volt, a transconductance G m  for the transconductor  824  of 185 micro-amperes per volt, a transconductance QG m  for the transconductors  834  and  844  of 1210 micro-amperes per volt, and a capacitance for the capacitors  816 ,  854  of 126 picofarads. The output  1420  of the third on-off Tow-Thomas biquad  1418  corresponds to output  1422  of the sixth order bandpass Chebychev filter  1400 .  
         [0200]    In a further exemplary embodiment, the signal processing circuit  604 , shown in FIG. 6, can be a sixth order bandpass Chebychev filter  1450 , shown in FIG. 14( b ), with a ripple of 0.25 dB, a bandwidth of 0.5 MHz. The sixth order bandpass Chebychev filter  1450  can have a center frequency of 1.25 MHz. The sixth order bandpass Chebychev filter  1450  is constructed by connecting three on-off Tow-Thomas biquads together in series.  
         [0201]    Referring to FIG. 14( b ), a signal received by the input  1452  of the sixth order bandpass Chebychev filter  1450  is conveyed to an input  1454  of a first on-off Tow-Thomas biquad  1456 . Assuming that it is turned on, The first on-off-Tow-Thomas biquad  1456  processes the signal received at the input  1454  and provides a signal at an output  1458 . The first on-off Tow-Thomas biquad  1456  that is turned on advantageously has a transconductance G in  for a transconductor  808  of 72.9 micro-amperes per volt, a transconductance G m  for a transconductor  824  of 70 micro-amperes per volt, a transconductance QG m  for transconductors  834  and  844  of 223.5 micro-amperes per volt, and a capacitance for capacitors  816 ,  854  of 29 picofarads. The output  1458  of the first on-off Tow-Thomas biquad  1456  corresponds to input  1460  of a second on-off Tow-Thomas biquad  1462 .  
         [0202]    Assuming that it is turned on, the second on-off Tow-Thomas biquad  1462  processes the signal received at the input  1460  and provides a signal at an output  1464 . The second on-off Tow-Thomas biquad  1462  that is turned on advantageously has a transconductance G in  for the transconductor  808  of 114.4 micro-amperes per volt, a transconductance G m  for the transconductor  824  of 70 micro-amperes per volt, a transconductance QG m  for the transconductors  834  and  844  of 458 micro-amperes per volt, and a capacitance for the capacitors  816 ,  854  of 74 picofarads. The output  1464  of the second on-off Tow-Thomas biquad  1462  corresponds to the input  1466  of a third on-off Tow-Thomas biquad  1468 .  
         [0203]    Assuming that it is turned on, the on-off Tow-Thomas biquad  1468  processes the signal received at the input  1466  and provides a signal at an output  1470 . The third on-off Tow-Thomas biquad  1468  that is turned on advantageously has a transconductance G in  for the transconductor  808  of 283 micro-amperes per volt, a transconductance G m  for the transconductor  824  of 70 micro-amperes per volt, a transconductance QG m  for the transconductors  834  and  844  of 458 micro-amperes per volt, and a capacitance for the capacitors  816 ,  854  of 48 picofarads. The output  1470  of the third on-off Tow-Thomas biquad  1468  corresponds to output  1472  of the sixth order bandpass Chebychev filter  1450 .  
         [0204]    Referring to FIG. 22, there is shown an exemplary transconductor  2200  that may be used to implement the on-off Tow-Thomas biquads of FIGS.  14 ( a ) and  14 ( b ). The transconductor  2200  is identical to the transconductor  900  shown in FIG. 9, except for the addition of a PMOS transistor Q 7  and an NMOS transistor Q 8 . The PMOS transistor Q 7  is connected in series between the gate  917  of the PMOS transistor Q 5  and ground. The NMOS transistor Q 8  connected in series between the gate  920  of the NMOS transistor Q 6  and the gate  917  of the PMOS transistor Q 5 . If the PMOS transistor Q 7  is turned off and the NMOS transistor Q 9  is turned on by the application of a logical one voltage to the gate terminal  2204 , the transconductor  2200  operates in essentially the same manner as the transconductor  900  shown in FIG. 9. However, the PMOS transistor Q 7  is turned on and the NMOS transistor Q 8  is turned off by the application of a logical zero voltage to the gate terminal  2204 , the transconductor  2200  is disabled and the output  810  of the transconductor  2200  acts as an open circuit. Each transconductor of the on-off Tow-Thomas biquad may have the configuration of the transconductor  2200 , and the gate terminal  2204  of each transconductor may be connected together to provide a terminal for turning each of the Tow-Thomas biquads on or off.  
         [0205]    In a further exemplary embodiment, the signal strength detector  608  is described in FIG. 12( b ) as signal strength detector  1250 . The input  641  of the signal strength detector  608  corresponds to the input  1252  of the signal strength detector  1250 , the input  641  of the signal strength detector  608  corresponds to the input  1253  of the signal strength detector  1250 , and the output  611  of the signal strength detector  608  corresponds to the output  1270  of the signal strength detector  1250 .  
         [0206]    A signal received by the input  1252  of the signal strength detector  1250  is conveyed to an input  1254  of a peak detector  1256 , which is similar to the peak detector  1180  as shown in FIG. 11. The peak detector  1256  processes the signal received at the input  1254  and provides a signal at an output  1258 . The output  1258  of the peak detector  1256  corresponds to input  1260  of a threshold detector  1262 .  
         [0207]    The threshold detector  1262  processes the signal received at the input  1260  and provides a signal at an output  1264 . The threshold detector  1262 , which is similar to the first threshold detector  1175  shown in FIG. 11, is configured by setting a reference current of a current source  1170  (shown in FIG. 11) to detect the first limit, which represents the minimum tolerable signal to noise ratio of the filter  604 . The reference current representing the first limit for the threshold detector  1262  can be 30 micro-amperes. The threshold detector  1262  processes the signal at its input  1260  and transmits a signal at its output  1264 . The output  1264  of the threshold detector  1262  is connected to an input  1266  of a two input OR gate  1268 .  
         [0208]    A signal received by the input  1253  of the signal strength detector  1250  is conveyed to an input  1255  of a peak detector  1257 , which is similar to the peak detector  1180  as shown in FIG. 11. The peak detector  1257  processes the signal received at the input  1255  and provides a signal at an output  1259 . The output  1259  of the peak detector  1257  corresponds to input  1261  of a threshold detector  1263 .  
         [0209]    The threshold detector  1263  processes the signal received at the input  1261  and provides a signal at an output  1265 . The threshold detector  1263 , which is similar to the first threshold detector  1175  shown in FIG. 11, is configured by setting a reference current of a current source  1170  (shown in FIG. 11) to detect the second limit, which represents the saturation point of the filter  605 . The reference current representing the second limit for the threshold detector  1263  can be 7.7 micro-amperes. The threshold detector  1263  processes the signal at its input  1261  and transmits a signal at its output  1265 . The output  1265  of the threshold detector  1263  is connected to an input  1267  of a two input OR gate  1268 . The two input OR gate  1268  processes the signals received at its inputs and provides a signal to the output  1270  of the signal strength detector  1250 .  
         [0210]    In a further exemplary embodiment, the timer  610  can be the timer  1300  as shown in FIG. 13. The input  639  of the timer  610  corresponds to input  1302  of the timer  1300 , and the outputs  635 ,  637 ,  631 ,  633 , of the timer  610  correspond to outputs  1309 ,  1319 ,  1394 ,  1399 , respectively, of the timer  1300 . The n-bit overflow counter  1388  should be configured to allow a period of time to elapse that is at least as long as the longest amount of time it takes for transients at the output of a signal processor circuit after it is turned on to die out before the counter overflow output  1389  changes from a logical zero to a logical one. The outputs  587 ,  589 ,  591  are not connected when the timer  1300  is used with the system  600 .