Abstract:
A system and method for performing a test for characterizing high frequency operation of PCB boards. More particularly, a system and methodology is provided to implement a time-domain short pulse propagation (SPP) technique on the production line, on large, multi-layer, product-level PCB boards, for large volume testing, by people who are not familiar with advanced, delicate, measurement techniques, who need robust test facilities, and cannot afford the time or expense of other lab-type approaches.

Description:
BACKGROUND OF THE INVENTION 
     1. Field of the Invention 
     The present invention relates generally to systems and techniques for modeling and characterizing printed-circuit board wiring, and particularly, to an improved system and method for generating more accurate transmission line models and characterizations for predicting performance of circuits and circuit structures as printed-circuit board transmission data-rates increase. 
     2. Description of the Prior Art 
     There currently exists limited techniques for providing time and frequency domain measurements from which transmission line models and material parameters for characterizing high frequency performance of printed-circuit board (PCB) conductor structures (i.e., transmission lines) may be extracted. 
     One particular technique, known in the art as short-pulse-propagation, SPP, is a time-domain technique that may be employed to model and characterize performance of circuits and circuit structures. As described in the reference to A. Deutsch, R. S. Krabbenhoft, et al. entitled “Practical Considerations in the Modeling and Characterization of Printed-Circuit Board Wiring”, Digest of SPI&#39;06, Signal Propagation on Interconnects, May 10-13, 2006, Berlin, pp. 1-4, incorporated by reference herein, the SPP technique requires propagating a short, electrical pulse along two identical transmission lines with different lengths, l 1  and l 2 . In current practice, the short pulse is generated by differentiating the step-source of a sampling oscilloscope. 
       FIG. 1  depicts an exemplary prior art measurement apparatus  10  for characterizing high frequency performance of a non-production level (test) PCB showing a short pulse generating source  12  feeding test pulse signals to coaxial probes  16  for differential measurement. The prior art set-up depicted in  FIG. 1  is a bench-test set-up configured to conduct a time domain transmission (TDT) measurement technique by launching a short, electrical pulse onto a transmission-line structure on the PCB and measuring the pulse signals to compute characterizing data. In one embodiment, using the test set-up  10  shown in  FIG. 1 , the test pulse signals are obtained by differentiating the step-source of a sampling oscilloscope  12  (e.g., an HP model 54120A) using a passive impulse-forming network  17 . In one embodiment, source pulses are, for example, 35 ps and 29 ps (obtained with the Picosecond Pulse Labs pulse generator 4015C and the 5208 network) width and are launched on respective transmission-line structures of different line lengths via test pads formed on the surface of the PCB. High-speed coaxial probes  16  in ground-signal (GS) configuration, (GGB Industries model 40A, 15OLP) are used to connect to the transmission-lines via test pads. In  FIG. 1 , a 50-GHz sampling oscilloscope  12  uses a detector channel, e.g., with 2.4 mm connectors and 40 GHz flexible coaxial cables  19  (e.g., Gore GD/AJ, 160-mil-diameter) between the probes  16  and the oscilloscope  15 . 
     Although not shown in  FIG. 1 , the test set-up  10  is further configured to provide at the PCB a parallel-plate device by which a low-frequency capacitance measurement may be made by a low frequency impedance analyzer. More particularly, according to the prior art, the line self and mutual capacitances are able to be measured and modeled, e.g., at 1 MHz as is the effective dielectric constant of region around the lines. 
     In accordance with the SPP technique using the apparatus depicted in  FIG. 1 , the transmitted pulses are detected and digitized. A time window technique is applied to the pulses to eliminate unwanted reflections from the measurement probes, any contact pads and vias, and cable connectors. In exemplary embodiments, a rectangular time window is used with a smooth transition to the signal baseline steady-state level since the amplitude resolution is more essential than the spectral resolution for this technique. A Fast Fourier Transform (FFT) is performed on the processed waveforms to obtain the complex propagation constant Γ(f) set forth in equation (1): 
                     Γ   ⁡     (   f   )       =         α   ⁡     (   f   )       +     j   ⁢           ⁢     β   ⁡     (   f   )           =         1       l   1     -     l   2         ⁢     ln   ⁡     (         A   1     ⁡     (   f   )           A   2     ⁡     (   f   )         )         +     j   ⁢           Φ   1     ⁡     (   f   )       -       Φ   2     ⁡     (   f   )             l   1     -     l   2                       (   1   )               
where α(f) and β(f) are the attenuation and phase constant, respectively, of the transmission line as a function of frequency (f), and, A i (f) and Φ i (f) are the respective amplitude and the phase of the transforms corresponding to the lines with lengths of l 1  and l 2  and l 1 &gt;l 2 . As referred to herein, frequency is referred to as a variable “f” or “ω”.
 
     From the ratio of the two Fourier transforms, the broadband attenuation and phase constant is extracted. No de-embedding or calibration is needed as in frequency-domain based techniques using Vector-Network Analyzers, VNA. The per-unit-length R(f), L(f), C(f), G(f) parameters (R is resistance, L is inductance, C is capacitance, and G is conductance) for the transmission line structure are then calculated using the dimensions obtained by cross sectioning the PCB hardware. This calculation is performed by using an (electromagnetic) field solver that also requires the metal resistivity information of the T-line structures. This metal resistivity information is obtained in accordance with equation (2) by performing a four-point resistance measurement of the two lines and using the actual dimensions, 
                   R   =       ρ   ⁢           ⁢   l     A             (   2   )               
where R is the resistance of the conductor and p is the resistivity, l is the length and A the cross-sectional area of the T-line conductor.
 
     The initial calculation of the per-unit-length R(f), L(f), C(f), G(f) parameters for the transmission line structure is performed with an initial estimation of dielectric constant and dielectric loss. For the low frequency range of 10 KHz to 1 MHz, actual measurements of dielectric loss can be made on a large parallel plate structure embedded on the same PCB structure with the signal layer of interest. 
     The dielectric constant “∈” at 1 MHz can be reliably measured from the capacitance measurement on the parallel plate structure of the PCB in accordance with equation (3): 
                   C   =         ɛ   0     ⁢     ɛ   r     ⁢   A     h             (   3   )               
where C is the capacitance, ∈ r  the relative permittivity, ∈ o  the absolute permittivity, A the plate area, and h is the thickness of the dielectric. In current practice, for the signal transmission frequency range between 1 GHz to 50 GHz, an initial guess is made. An electromagnetic field solver is implemented to fit a range of values for the complex permittivity using this initial guess. The attenuation and phase are then calculated based on the R, L, C, G values. The calculated and measured values are compared, and, the procedure is repeated until good agreement is obtained. Each time, the dielectric loss is changed.
 
     The field solver generates causal results for C(f) and G(f) based on a Debye model for the complex permittivity: 
                     ɛ   ⁡     (   ω   )       =       ɛ   ∞     +       ∑   i     ⁢       ɛ   i       1   +     j   ⁢           ⁢   ω   ⁢           ⁢     τ   i                       (   4   )               
where ∈ i  ∈ ∞  and τ i  are parameters or the expansion in accordance with the Debye model.
 
     The final C(f) and G(f) are used, together with the measured ∈ r  and the calculated C at 1 MHz, to obtain a measure of the broadband complex permittivity in accordance with equations (5). 
                         ɛ   r     ⁡     (   ω   )       =       (       C   ⁡     (   ω   )         C     1   ⁢           ⁢   MHz         )     ×     ɛ     r   ⁢           ⁢   1   ⁢           ⁢   MHz           ⁢     
     ⁢       tan   ⁢           ⁢     δ   ⁡     (   ω   )         =       G   ⁡     (   ω   )         ω   ⁢           ⁢     C   ⁡     (   ω   )                     (   5   )               
where ω is the frequency and tan δ a measure of dielectric loss.
 
     The broadband characteristic impedance Z o  is now obtained from equation (6): 
     
       
         
           
             
               
                 
                   
                     Z 
                     0 
                   
                   = 
                   
                     
                       Γ 
                       ⁡ 
                       
                         ( 
                         ω 
                         ) 
                       
                     
                     
                       
                         G 
                         ⁡ 
                         
                           ( 
                           ω 
                           ) 
                         
                       
                       + 
                       
                         j 
                         ⁢ 
                         
                             
                         
                         ⁢ 
                         ω 
                         ⁢ 
                         
                             
                         
                         ⁢ 
                         
                           C 
                           ⁡ 
                           
                             ( 
                             ω 
                             ) 
                           
                         
                       
                     
                   
                 
               
               
                 
                   ( 
                   6 
                   ) 
                 
               
             
           
         
       
     
     It is the case that typical VNA based measurements can generally obtain attenuation and phase, especially for high frequency range, but Z o (f) cannot be extracted due to the large discontinuities found in realistic multi-layer printed-circuit-boards, PCBs. As was demonstrated in the reference to T-M. Winkel, et al., entitled, “Comparison of Time- and Frequency-Domain Measurement Results for Product Related Card and MCM Transmission Lines up to 65 GHz”, Proc. Dig. IEEE 14 th  Top. Mtg Elec. Perf. of Electronic Packaging, Austin, Tex., Oct. 24-26, 2005, pp. 21-24, the current de-embedding and calibration techniques cannot compensate for the large end effects, i.e., the capacitance, resistance, inductance of the via, test pads, and probes. 
     As data rates transmitted on printed-circuit-boards increase from 2 Gbps to 20 Gbps and beyond, there is required more accurate and causal transmission line models for predicting system performance. Non-causal models can cause inaccurate signal integrity and timing prediction and simulator convergence problem. In order to generate broadband causal models (DC to ˜50 GHz) there is needed higher accuracy and higher-bandwidth measurements of dielectric constant ∈ r (f) and dielectric loss tan δ(f). Single value ∈ r  and tan δ that are typically supplied by vendors cannot generate causal models. The current practice for monitoring the integrity of production level printed-circuit boards is to measure the Z o  obtained from TDR measurements using a single, hand-held probe. One such prior art probe for TDR measurements is a hand-held probe  80  provided by Polar Instruments Ltd. (Beaverton Oreg.) such as depicted in  FIG. 8A  with its cover removed. In this embodiment, a Polar generated step source for conducting the TDR measurement has an approximate 120 ps-200 ps rise-time. Additionally, a 10 mil pitch coaxial probe  85  additionally shown in  FIG. 7A  can also be used for high-speed measurements as these types of coaxial probes may generate 1 ps-35 ps transitions. Further, the hand-held probes  80  include the probe tips  87  depicted in  FIG. 7B  with a 100 mil pitch as shown in close-up view. 
     Thus, currently, ∈ r  and tan δ values are generally supplied only at a few frequencies and measured on simple, non-representative structures. However, it is the case that such measurements are required to be made on multi-layer configurations and the data is needed over a wide frequency range such as from DC to 50 GHz. In addition, as higher-performance systems need the development of lower loss materials, these new materials need to be analyzed in representative, multi-layer structures. Furthermore, concerns to be considered such as losses due to roughness that could become significant, in the order of 5-50% loss increase at 5 GHz, for example. Further considerations to be accounted for include: moisture absorption of new materials that impacts reliability. Further, lead-free compatibility imposes manufacturing constraints that impact electrical characteristics. 
     Moreover, simple TDR production-level Z o  process monitors need to be improved because such techniques overpredict Z o  due to losses on the board wiring. Overprediction of Z o  affects board design, cost, wireability, and system power. Thus, Z o  extraction needs to be extended to broadband phase constant Γ(f) and broadband characteristic impedance Z o (f). 
     It would be highly desirable to provide an improved test apparatus that can extend this measurement capability to multi-layer production level PCB boards by providing at least two lines of different lengths and utilizing better probes, improved structures, and instrumentation. 
     It is desired that such improved testability further maintain the ruggedness commensurate with production level testing. 
     SUMMARY OF THE INVENTION 
     The present invention is directed to a system and methodology that incorporates advanced measurement techniques for extracting electrical characteristics of interconnects on multi-layer production level printed circuit boards. 
     Bringing such test capability into the production environment is currently unique to this methodology which includes incorporating, on large multi-layer production level PCB boards, a simple structure that includes the lines of different lengths. Only a minimum of two such lines are needed. For full characterization, a large circular plate is also added to the large multi-layer production level PCB board. 
     According to an aspect of the present invention, there is provided a system and method of testing a multi-level printed circuit board (PCB) having one or more layers of conductors carrying signals at or exceeding Gigahertz frequencies. The testing method comprises:
         providing, at a layer of the multi-level PCB board, a test structure comprising:
           a first conductor line, of x length and a second conductor line formed at a same layer of y length where x&gt;y; and, each first and second conductor line having respective capture pad termination at each end; and,   a plated via through hole extending between a formed surface test pad connector at a surface of the PCB for electrically coupling respective first and second capture pad terminations at each line end to a respective surface test pad connector provided at a PCB surface, each test pad connector configured for electrical coupling to an RF connector device at the PCB board surface,   
           automatically coupling a first RF connector device to a respective surface test pad connector via an RF connector device at a first end of a conductor line and a second RF connector device to a respective surface test pad connector at a second end a conductor line;   automatically configuring a testing apparatus for testing the conductor line formed at the layer by inputting signals at a first end of the conducting line via the first RF connector device coupled to a first surface test pad connector at a PCB surface and, measuring signals at a second end of the conducting line via the second RF connector device coupled to a second surface test pad connector at the PCB surface, the testing implementing a time-domain Short Pulse Propagation (SPP) technique; and,   processing, at a computing device, the measured signals for modeling performance of the PCB when operating in excess of Gigahertz frequencies.       

     Further to this aspect of the invention, the testing apparatus comprises first and second mounting devices rigidly holding the first and second RF connector devices, a platform for engaging the multi-level PCB, and an indexing means carrying for automatically aligning the platform carrying the multi-level PCB with the first and second RF connector devices and automatically coupling the first and second RF connector devices to respective first and second surface test pad structures. 
     Alternatively, the testing apparatus comprises first and second robotic manipulator arms holding respective the first and second RF connector devices, the method further comprising: automatically coupling the first and second RF connector devices held by the robotic arms to respective surface test pad structures of the multi-level PCB. 
     In a further aspect of the invention, a portion of the plated via through hole extending between a formed surface test pad connector at one of a top or bottom PCB surface and a conductor line capture pad at a signal line layer beneath the PCB surface includes a stub portion, the test method further comprising: 
     during the testing, coupling the RF connector devices to a surface test pad connector that minimizes a length of the stub portion. 
     In one embodiment, the PCB is a production-level PCB, the computing device processing the measured signals for extracting a broadband propagation constant and characteristic impedance of the conductor line structures useful for the performance modeling. 
     In one embodiment, the PCB is a production-level PCB, the computing device processing said measured signals for extracting a broadband attenuation and phase constant of said conductor line structures useful for said performance modeling. 
     According to another aspect of the invention, there is provided a test structure for facilitating performance testing of a multi-level printed circuit board (PCB) having one or more layers of conductors carrying signals at or exceeding Gigahertz frequencies, the testing structure comprises: 
     a first conductor line formed at a layer of the multi-level PCB board, of x length and a second conductor line formed at a same layer of the multi-level PCB board, of y length where x&gt;y; and, each first and second conductor line having respective capture pad termination at each end; and, 
     a plated via through hole extending between a formed surface test pad connector at a surface of the PCB for electrically coupling respective first and second capture pad terminations at each line end to a respective surface test pad connector provided at a PCB surface, each test pad connector configured for electrical coupling to an RF connector device at the PCB board surface, 
     wherein a test apparatus models performance of the PCB when operating in excess of Gigahertz frequencies by coupling signals to and from a conductor line via the RF connector device and automatically performing a time domain single pulse propagation measurement of the conductor lines at a PCB layer. 
     The test structure further comprises: formed at the same layer of the multi-level PCB board, a capacitor structure having corresponding surface test pad structure being electrically coupled to the capacitor structure through a respective plated via through hole and configured for electrical coupling to the RF connector device. 
     In one embodiment, the plated via through hole extends between front and back PCB surfaces, a test pad connector provided at both front and back PCB board surfaces. 
     Further, the first and second conducting lines are each formed at multiple layers of a PCB, each conductor line at each layer having a respectively formed PTH via connection to a respective test pad connector formed at a PCB surface. 
     Further, a portion of the plated via through hole extending between a formed surface test pad connector at one of a top or bottom PCB surface and a conductor line capture pad at a signal line layer beneath the PCB surface includes a stub portion, wherein, during the testing, the RF connector devices coupled to a surface test pad connector that minimizes a length of the stub portion. 
     According to a further aspect of the invention, there is provided a method of forming a test structure for a multi-level printed circuit board (PCB) having one or more layers of conductors carrying signals at or exceeding Gigahertz frequencies, the method comprising: 
     forming at a layer of the PCB board, a first conductor line of x length and a second conductor line of y length where x&gt;y; and, each first and second conductor line having respective capture pad termination at each end; 
     forming, at each top and bottom PCB surface, a respective surface test pad connector structure in alignment with a corresponding capture pad termination at each conductor line end, and configured for electrical coupling to an RF connector device at the PCB board surface; 
     forming a respective via through hole extending between a formed surface test pad connector at the top and bottom surfaces of the PCB, the formed via hole intersecting a respective capture pad termination of each the conductor line; and, 
     plating the via through hole for electrically coupling a respective first and second capture pad termination of a conductor line to a respective surface test pad connector. 
     Advantageously, the system and method of the present invention enables testing of PCBs in a production level environment. In such environments, very thick boards are tested with very long plated through-hole (PTH) vias. Testing may be performed on many boards within short time by operators who are not familiar with advanced, delicate measurement technique. The set-up is automated or semi-automated for large volume, fast testing and robust for rough handling. 
    
    
     
       BRIEF DESCRIPTION OF THE FIGURES 
       The features and advantages of the present invention will become apparent to one skilled in the art, in view of the following detailed description taken in combination with the attached drawings, in which: 
         FIG. 1  is a prior art depiction of a bench test set-up  10  for providing and measuring short pulses propagated on transmission line structures in an example application of an SPP technique; 
         FIG. 2  is a plot  20  depicting two short pulses propagated on the transmission lines in an example application of the SPP technique utilizing the production-level test set-up of  FIGS. 13A ,  13 B in one embodiment of the invention; 
         FIG. 3  is an example plot depicting an example measured and fitted attenuation (dB/cm) up to 50 GHz for an example PCB transmission line structure using the production-level test set-up of  FIGS. 13A ,  13 B in one embodiment of the invention; 
         FIG. 4  is an example plot depicting an example fitted and measured phase constant (1/cm) up to 50 GHz for an example PCB transmission line structure using the production-level test set-up of  FIGS. 13A ,  13 B in one embodiment of the invention; 
         FIG. 5  is an example plot depicting the extracted broadband permittivity ∈(ω) up to 50 GHz for the example PCB transmission line structure using the production-level test set-up of  FIGS. 13A ,  13 B in one embodiment of the invention; 
         FIG. 6  is an example plot depicting an example extracted broadband characteristic impedance (Ohms) as a function of frequency showing both real and imaginary components in an example implementation of the SPP measurement techniques employed in the production-level test set-up of  FIGS. 13A ,  13 B; 
         FIG. 7A  depicts a 100 mil pitch bandheld coaxial probe; and,  FIG. 7B  depicts a close up view of the 100 mil pitch tips used for high-speed measurements in accordance with the prior art; 
         FIG. 8  is in top view of a test coupon structure having various line lengths and parallel plate structure according to one embodiment of the invention; 
         FIG. 9A  shows an enlarged close-up view of an example top view of a test pad structure for connecting to an RF connector device formed at the top surface of the PCB; and,  FIG. 9B  shows an enlarged close-up view of an example bottom view of the test pad structure of  FIG. 9A , formed at the bottom surface of the PCB; 
         FIG. 10  shows a typical SMA connector in both front and back perspective views; 
         FIG. 11  depicts a side view of an SMA connector showing alignment screws/posts inserted into the SMA connector at respective alignment holes for mating an SMA connector with a test pad provided at each end of the conductor line; 
         FIG. 12  illustrates a production level test set-up depicting a semi-permanent attachment of surface-mount SMA connector functioning as a probe that can easily be mounted and dismounted onto a respective surface test pad according to one aspect of the present invention; 
         FIG. 13  illustrates conceptually an example production level test set up for automated SPP testing of production level PCB using a computer device programmed to implement the methodology depicted in  FIG. 15  according to the invention; 
         FIG. 14  is a diagram depicting a cross-sectional view of an example multi-level PCB board including the test coupon and PTH (plated through hole) vias for test measurements according to one aspect of the invention; 
         FIG. 15  depicts a methodology  300  for conducting the short-pulse-propagation, SPP, time-domain technique using the test apparatus of  FIG. 14  in accordance with the invention; and, 
         FIG. 16  shows a virtual test bench technique  400  that may be used to quantify the performance of a device, evaluate and virtually reconstruct SPP process, and define the allowable fabrication tolerances in production; and, 
         FIG. 17  shows a cross-sectional view of a modeled virtual lossy stripline  410  of  FIG. 16 . 
         FIG. 18  depicts and exemplary computer system  500  including one or more processors or processing units, a system memory, and an address/data bus structure that connects various system components together. 
     
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     A preferred embodiment of the invention consisting of a description of the method employed and the necessary apparatus will now be described. 
     In one embodiment, a system and methodology of incorporating advanced measurement techniques for extracting electrical characteristics of interconnects on multi-layer production level printed circuit boards is provided. Bringing such test capability into the production environment is unique to this methodology. 
       FIG. 8  depicts a top view of a portion of a large production level PCB board  99 . In an example embodiment, the PCB board in  FIG. 8  is a large functional board, e.g., about ⅕ to ¼ inches thick and about 20 in. by 14 in. in area, for example, and may comprise a blend of glass fiber weave and epoxy-resin (e.g., bismaleimide triazine (BT)) as a substrate for use in printed circuit board wiring. According to the invention, the production board  99  is manufactured to include a test coupon  100  of small footprint including two or more conducting line structures, each line of different lengths manufactured on the PCB surface  98 . For example, the coupon size may be about 2.54 cm×16 cm having at least two such conducting lines  102 ,  104  of 3 cm and 10 cm in length, respectively. As shown in the top view of the PCB of  FIG. 8 , the coupon may include additional line structures formed of alternate lengths, e.g., 1 cm, 5 cm, etc. Conductor line materials typically include Cu, however, may include other conductive materials, e.g., alloys of copper. Conductor lines may include transmission lines (T-line) including microstrip and stripline structures capable of carrying digital signals at Gigahertz frequencies. For fill characterization, the coupon structure  100  includes a capacitor structure, e.g. plate  120  having the PCB substrate material as a dielectric. In one embodiment, the capacitor  120  includes a plate structure of a diameter between 50×-100× the height of insulator, e.g., 500-mil in diameter, having probe contacts, such that, a capacitive measurement may be performed at relatively low frequency, e.g., to calculate the dielectric constant. In one embodiment, the capacitor plate structure depicted in  FIG. 8  is used for extracting dielectric constant at a frequency of 1 MHz, for example. 
     The insulator between the plate  120  and the ground planes above and below the signal layer is the same as the dielectric with glass fiber composition found around the signal conductors of the stripline. Example dielectric constants at 1 MHz are in the range of 3 to 5. The diameter of the plate is 50-100× the height between the plate and the ground plane. This height is in the range of 3 to 5 mil. The signal line widths are in the range of 3 to 5 mil with thickness of 0.7 to 1.4 mil.  FIG. 8  also shows the connection to the ground planes and dummy structures that duplicate the connection to the plate but without the plate present. Both the plate and the dummy structure capacitances are measured and the final capacitance value calculated according to equation (3) is the difference between these two measurements. 
     As further shown in  FIG. 8 , each line  102 ,  104  of the coupon  100  includes a respective surface test pad  105 ,  110  at each respective conductor line end for accommodating an RF/microwave frequency contact used for bandwidth applications (up to ˜50 GHz) as test probes. In accordance with one embodiment of the invention, the testing structure implements high performance SMA-type connectors, however, it is understood that other connectors of coaxial probes can be used. In one example, with a step excitation, the SMA probe can transmit a pulse in the production environment. 
       FIG. 9  shows enlarged close-up views of an example test pad structure  105  connecting a conductor or T-line formed in a test coupon  100  of  FIG. 8  and particularly, a single test pad structure  117  shown at a top view of the PCB board (shown in  FIG. 9A ) and a test pad structure  119  shown at a bottom view of the PCB board (shown in  FIG. 9B ). In one embodiment, for example, each SMA connector test pad  105 ,  110  includes alignment holes  112   a, b , for mating with an SMA connector such as SMA connectors  125  shown in both front and back perspective views as depicted in  FIG. 10 . The test pad  105 ,  110  alignment holes, in one embodiment, may be dimensioned as 1.575 mm [0.062 in] in diameter on, for example, a 6.99 mm [0.275 in] pitch, for accommodating mating of an SMA connector  125 . 
     As shown in  FIG. 11 , for testing/measurement, a pair of set screws or other threaded posts  127   a ,  127   b  are inserted into the SMA connector  125  at each respective alignment hole  112   a ,  112   b  in order to mate a respective SMA connector with the test pad  105 ,  110  provided at each end of the conductor line. In the embodiment depicted in  FIG. 11 , a set screw/post that is inserted into the SMA may be dimensioned as 3.175 mm [0.125 in.] in length and 1.473 mm [0.058 in.] in diameter. Thus, in the embodiment depicted in  FIG. 11 , the set screws/posts may extend beyond, e.g., protrude 0.89 mm [0.035 in] below the surface of the SMA connector and function as mechanical alignment pins that can be slip-fit into the holes  112   a ,  112   b  in the card shown in the example test set-up shown in  FIG. 12  and enable the SMA to function as a probe, rather than as a bolted permanent SMA connection. 
       FIG. 12  particularly illustrates an example test fixture  150  including a semi-permanent attachment of two surface-mount SMA connectors  125   a ,  125   b  that can be mounted and dismounted onto a respective test pad  105 ,  110 . In one embodiment, the mounting and dismounting may be automated, e.g., performed by lowering or raising the height of a holding base or platform  152  upon which the PCB board  99  under test is mounted. That is, in one embodiment, during a PCB production level test run, an indexing mechanism (not shown) is provided for lifting the board  99  into position, and the respective SMA connectors  125   a ,  125   b , which are each rigidly held by a respective mounting arm  135   a ,  135   b  in spaced apart relation (e.g., 3 cm or 10 cm) to accommodate the particular T-line line lengths of the coupon, is inserted into the holes with the set screws for surface mounting of the SMA connector  125  to a respective test pad. The SMA connectors  125   a,b  are themselves electrically coupled to test equipment by attaching RF cabling  140  to a coaxial adaptor  145  that mates with the mounted SMA connector. 
     It is understood that, in an alternative embodiment, the test fixture  150  may provide for the SMA connector to be mounted and dismounted onto a respective coupon test pad by automatically indexing (lowering or raising) a robotic arm holding the SMA connector itself until the held SMA connector itself mates to the test pad formed in the PCB board  99  test coupon. In one embodiment, the test fixture provides robotic/automated manipulators used to automatically place the probes along the surface of the large board. The manipulators are programmed to move along the large surface of the board to get to the correct position. Further, alternatively, the probe arm engaging the SMA connector may be manually indexed for mating the SMA connector within the respective test pad structure of a production level PCB, e.g., using a hand-held type probe (not shown). 
       FIG. 13  illustrates conceptually an example production level test set up for automated SPP testing of production level PCB. That is, the automated production-level testing implements computer device  500  for controlling both the 50-GHz sampling oscilloscope  12  for TDT measurements and a low frequency impedance analyzer  11  for capacitive measurements to perform the SPP production-level test methodology of the invention described in greater detail with respect to  FIG. 15 . 
     As mentioned herein above, a small portion of the PCB board space is for the coupon structures. In one embodiment, for a multi-level PCB having functional circuits on various levels, the conductor lines  102 ,  104  (or, like conductor “trace” structures) are formed on one or more specific layers. The same pattern is repeated for each layer and placed at various locations to check tolerances, which facilitate use of the coupon  100  that can be probed at the board surface to output data used in the SPP testing. 
       FIG. 14  is a diagram depicting a cross-sectional view of an example PCB board  199 . In the embodiment of PCB  199  depicted, thirteen (13) levels (layers)  201 - 213  are provided with layers  201 ,  203 ,  205 ,  207 ,  209 ,  211  and  213  being electrical signal conducting layers and layers  202 ,  204 ,  206 ,  208 ,  210  and  212  being ground layers or ground planes. Signal conductor lines  201 ,  205 ,  209  and  213  are signal interconnects in the X-axis direction, for example, while, signal conductor lines  203 ,  207  and  211  are signal interconnects in the Y-axis direction, for example. It is understood that each of signal lines  201 ,  203 ,  205 ,  207 ,  209 ,  211  and  213  are formed in an insulator or substrate material, e.g., a dielectric material  218  such as BT. In one embodiment, the PCB insulator material comprises a composite(s) of a glass-fiber weave embedded in an epoxy resin. In a further aspect of the invention, one or more signal layers of the multi-level PCB  199  is manufactured to have the test site of  FIG. 9  including the trace conductors (e.g., T-line structures) of 3 cm and 10 cm length and the capacitive plate structure. The test structure of lines and plate can be on any of the layers  201 ,  203 ,  205 ,  207 ,  209 ,  211 , and  213 . That is, the test site (coupon)  100  shown in  FIG. 9  may be manufactured at one or more of the signal layers of the multi-level PCB. Each test site includes a respective manufactured via connection, such as via connections  215 ,  220  for contacting a top layer SMA test pad  119  or bottom layer SMA test pad  117  to both ends of a respective trace. 
     In one embodiment, each via connection  215 ,  220  is manufactured as a Plated Through Hole (PTH) connector, particularly, by drilling a respective via hole structure all the way through each layer of the PCB board through so as to contact a trace or specifically, a capture pad or similar metal feature formed at the end of a trace, and then plating the formed via hole with conductive material, e.g., a metal such as copper, to render it as a PTH. As shown in  FIG. 14 , each PTH via  215 ,  220  extends from layer  201  to layer  213  of PCB  199  and includes as is shown contacting a capture pad  225  connecting a signal line at each end (only 1 is shown) to the test pads  117 ,  119 . More particularly, as shown in  FIG. 14 , a capture pad  225  is manufactured on the signal layer of interest. In the example PCB  199  depicted in  FIG. 14 , capture pads  225  are at the signal layer  203  and  211 . During manufacture, the PCB board is drilled first, the drill preferably having an example tolerance such that the diameter of the capture pad placed on the signal layer is about three times (3×) the via diameter, to ensure that even if the drill shifts, it will land on a large capture pad  225 . For example, in one embodiment, PTH via  215 ,  220  may be 12 mil in diameter while the capture pad diameter is 3× this value or more. Then, a conductor material, e.g., copper, is plated on the sides of the drilled via hole in order to malce electrical contact from the top surface test pad to the signal line at the layer of interest. 
     As shown in  FIG. 14 , there is additionally provided via stub portions  216 ,  221  of the total PTH via length that extends beyond the layer in which the conductor line resides. The length of each respective via stub portions  216 ,  221  extending beyond signal layer is shown in broken circles. That is, stub portions  216 ,  221  are the PTH via length portions from the capture pad  225  at a layer of interest, such as  211  or  203 , to the open end of PTH formed at the bottom surface of the PCB or such as layer  213  and pad  117 , or formed at the top of the board on layer  201  and pad  119  when probing is done from test pad  117  and capture pad  225  is used for layer  203  signal. 
     As the bandwidth of the SPP technique implemented in accordance with the invention is dependent on the ability of eliminating the effect of end parasitics by using the time windowing and ratioing of FFTs, it has been found that the length of the plated-through hole (PTH) will have the strongest effect, i.e., the propagated pulses with various via stub conditions. Due to this effect, the back drilling of the vias  215 ,  220  is performed as a cost effective means to increase the bandwidth, e.g., for lines placed on the middle layers of PCB boards, especially large PCB boards having typical thicknesses of about 100-200 mil, or more. That is, in one embodiment, after plating the entire via hole, “backdrilling” may be performed to remove a portion of the plated through hole that may be detrimental to accurate high frequency measurements as contributing to a long stub portion. Performing backdrilling to remove a lengthy stub portion of the PTH connected to the trace line will increase the bandwidth of a high-frequency measurement using the SMA connector probe such as contemplated by the invention. 
     Alternate means of reducing the PTH stubs include use of stacks of subcomposites or microvia technologies. Subcomposites are groups of a few layers only that are built independently and then joined with short PTH vias. Other approaches would join these sub-groups with conducting material and not use drilling. 
     In the example multi-level PCB  199  shown in  FIG. 14 , capture pads or similar feature  225  are provided at layers  203  or  211  connected to a trace. During testing operation, in one example scenario, the probing for signal line at layer  203  is performed from test pad  117  at layer  213  making the via stub  221  short. On the right side of the PCB depicted in  FIG. 14 , the testing for signal line at layer  211  is performed from the test pad  119  on layer  201  making the via stub  216  short. 
     Further, as shown in  FIG. 14 , in every layer that PTH via traverses, there is a gap between it and the ground planes referred to as an “antipad”. Metal material is only plated where the actual hole was drilled so that the via does not short to the ground but connects the outside test pad to the inner signal layer. An example signal path for testing, in one embodiment, starts from a test pad, e.g.,  119  on the right side of the PCB  199 , down through the PTH via to the layer of interest, e.g., layer  211 , propagate through the signal line at layer  211  on the left side of the PCB  199 , propagate through the PTH on the right and reach a second surface test pad, e.g., test pad  119  on the top left side of the PCB  199 . A line on PCB layer xx will be probed on the left and on the right, for input and output, from the same side of the board, either from layer  201  on both ends, or, from layer  213  on both ends of the line. 
     In alternate embodiment, for lines closer to the top or bottom layers of the PCB, e.g., within  40  mils from the PCB surface, probing is performed such that the stub length is minimal. Thus, for example, in a 10-layer PCB board, for lines in layers  201 - 203 , probing can be done at test pads from the backside of the board, while for layers  211 - 213 , probing is performed from the front of the board. 
     It is understood that, a similar PTH via connection is formed to connect a capacitor structure formed in the test coupon and embedded at a layer of the multi-level PCB to a surface test pad connection structure for connection to an RF connector device when making a capacitive test measurement, e.g., using an LCR multi-frequency meter (e.g., HP model 4275A). 
     Compensation of the PTH stub capacitance can also be made by enlarging the antipad size, further optimizing the launch structure and valid bandwidth of the resulting measurement. The optimal dimension can be determined by performing three dimensional modeling of the structure and simulating the entire measurement flow in a virtual test bench as will be described in greater detail herein below. The physical structure is modeled with a field solver. 
     The equivalent model is then included in SPICE type circuit simulation and virtual short pulse is injected into the two lines with these modeled via ends. The resultant pulses are then used in the signal processing software as if they were measured on actual hardware. The attenuation and phase are then extracted and the bandwidth is determined in a virtual mode. 
       FIG. 15  depicts a methodology  300  for conducting the short-pulse-propagation, SPP, time-domain technique employing the test coupon structure of  FIG. 9  on a product-level printed-circuit board such as shown in  FIGS. 12 ,  13 . A test apparatus configured as depicted in  FIGS. 12 and 13 , at a minimum, produces a short, electrical pulse propagating along the two identical transmission lines  102 ,  104  with different lengths, l 1  and l 2  at a test coupon provided at any level of the multi-level PCB. The SPP technique is used for both modeling and measurement of representative printed-circuit interconnect characteristics and their relevance for overall system performance. At a base level, the testing may be performed at the 3 cm and 10 cm traces of the test coupon of  FIG. 8  to garner information useful for calculating the transmission line attenuation and phase along the copper trace. By including the other structures in the test coupon of  FIG. 9 , e.g., capacitor plate  120 , additional information, such as the dielectric complex permittivity, can be extracted in the production environment and the user may incorporate other tests to provide more comprehensive information, e.g., that can be used for high frequency performance modeling. 
     As shown at step  301 , in  FIG. 15 , using the line traces in the test coupon structure at any PCB layer, the test method employing the computer or processor device  500  ( FIG. 13 ) implementing first programmed instructions for measuring the conductor&#39;s characteristic impedance Zo (not the broadband Zo(f) using a TDR (Time Domain Reffectometry) measurement. This initial screening enables selection of the two lines l 1  and l 2  that have similar Zo. The simple, single-frequency Zo testing of the prior art, is enhanced with the technique of the invention as it is now possible to perform attenuation measurement and ultimately extract the full broadband propagation constant Γ(f) and Zo(f) over the desired frequency range. 
     Thus, at step  303 , a DC measurement is performed to obtain line resistance in accordance with equation (2), and line capacitance at 1 MHz, and plate capacitance and dielectric loss measurements are made in accordance with equations (3) and (5). 
     A time domain transmission (TDT) step  305 , in  FIG. 15 , is then performed in order to obtain the two propagated pulses as shown in  FIG. 2  implemented in the SPP technique.  FIG. 2  is a plot  20  depicting two short pulses  22 ,  25  propagated on 2 cm and 8 cm long transmission lines respectively, in a current example application of the SPP technique utilizing the measurement apparatus  150  of FIGS.  12 , 13 . 
     In step  307 , the test equipment is configured to perform GammaZ signal processing of the propagated pulses to obtain the complex propagation constant Γ(f) as set forth in equation (1). This then allows the extraction of the complex permittivity, however, requires test line cross sectioning. At step  309 , the signal lines and parallel plate are cross sectioned at several locations and average dimensions are obtained to perform an initial calculation of the complex permittivity, e.g., at 1 MHz. 
     Continuing in accordance with the invention, the measurements may be extended to their full capability for extracting the full material properties of the insulator being used in the PCB. That is, while the SPP technique can be completed to the stage of extracting both the propagation constant and broadband impedance, the invention further allows the extraction of the complex permittivity. Such a step requires test line cross sectioning, calculation of R, L, C, G parameters with a field solver, measurement of the large plate loss tangent and capacitance at low frequency, and comparing of measured attenuation and phase to calculated values in an iterative manner as shown at step  325 . 
     Thus, continuing at step  310 ,  FIG. 15 , there is performed the calculation of R(f), L(f), C(f), and G(f) parameters using a causally-enforced field solver, CZ2D such as described in the reference to W. T. Weeks entitled “Calculation of coefficients of capacitance of multiconductor transmission lines in the presence of dielectric interface”, IEEE Trans. Mirowave Theory Tech., vol. MTT-18, pp. 35-43, 1970, and implementing the Debye model from equation (4). This leads to calculating the total attenuation α(f and β(f) at step  312  to extract the broadband complex permittivity in accordance with equation (5) and the characteristic impedance accordance with equation(6). It is understood that the C(f) and G(f) are calculated with CZ2D solver by using an initial set of values for the loss tangent of the dielectric, i.e., tan δ, using the permittivity value measured at 1 MHz as conducted at step  309 ,  FIG. 15 . Then at step  315 , the α(f) and β(f) complex propagation parameters extracted at step  307  are compared to the α(f) and β(f) values as calculated at step  312 . 
       FIG. 3  is an example plot  40  depicting an example measured and fitted attenuation (dB/cm) as a function of frequency (up to 50 GHz) for an example PCB transmission line structure using the automated production-level test set-up of  FIGS. 12 and 13 ; and,  FIG. 4  is an example plot  50  depicting an example fitted and measured phase constant (1/cm) as a function of frequency (up to 50 GHz) for an example PCB transmission line structure using the production-level test set-up of  FIGS. 12 and 13 . 
     Continuing, at step  316 , a determination is made as to whether the calculated values are acceptable, i.e., a good fit. If the calculated values are not a good fit, the process returns to step  310  to perform the calculation of R, L, C, G parameters with a field solver, and with adjusted parameters of the expansion (e.g., ∈ i  ∈ ∞  and τ i ) to improve the fit. Thus, as shown in  FIG. 15 , step  325  is understood that a few iterations may be made to fit the α(f) and β(f) complex propagation parameters to the measured values with each iteration adjusting the parameters of the expansion to improve the fit. In this iterative manner, a smooth interpolation and extrapolation is made over the desired frequency range (at step  320 ). 
     Remaining steps  325  are performed to obtain the full model in step  320 , including the step  317  of extracting the complex permittivity, loss tangent, and characteristic impedance over the desired frequency range, e.g., by relying upon equations (5) and (6) and also as explained in the herein incorporated reference to A. Deutsch, et al. entitled, “Extraction of ∈ r (f) and tan δ(f) for Printed Circuit Board Insulators Up to 30 GHz Using the Short-Pulse Propagation Technique”, IEEE Transactions on Advanced packaging, vol. 28, no. 1, pp. 4-12, February 2005. The extracted R(f), L(f), C(f), and G(f) are input to a Spice type circuit simulator to predict pulse and step signal propagation. These simulated waveforms are compared to actual measured TDT signals and step  318  in  FIG. 15  completes the correlation process. Since the R(f), L(f), C(f), and G(f) are produced by a field solver that enforces causality and the resultant waveforrns are verified with actual measurements, the transmission line models produced by the complete procedure in  FIG. 15  become reliable, predictive models for system performance prediction. For example,  FIG. 5  is an example plot  60  depicting the extracted broadband permittivity ∈(ω) as a function of frequency (up to 50 GHz) and  FIG. 6  is an example plot  70  depicting an example extracted broadband characteristic impedance (Ohms) as a function of frequency (up to 50 GHz) and showing both real  72  and imaginary  74  components for the example PCB transmission line structure using the production-level test set-up of  FIGS. 12 ,  13 . The extracted broadband characteristic impedance value is unlike the simple, single value Z o  obtained with typical time-domain reflectometry, TDR, measurements. 
     The SPP time-domain technique can successfully be used to extract the broadband permittivity for typical packaging interconnects. The technique is typically used on representative stripline structures built with small interface discontinuities such as pads and vias. A short pulse is injected into the two lines of different lengths. Signal processing of the digitized pulses consists of rectangular time windowing of the unwanted reflections from interface discontinuities and Fourier transformation. From the ratio of the two Fourier transforms the total attenuation α(f) and phase constant β(f) are obtained as shown at step  307 ,  FIG. 15 . 
     In sum, the SPP technique as described above can be completed to the stage of extracting both the propagation constant and broadband impedance. This then allows the extraction of the complex permittivity. Such a step requires test line cross sectioning, calculation of R, L, C, G parameters with a field solver, measurement of the large plate loss tangent and capacitance at low frequency, and comparing of measured attenuation and phase to calculated values in an iterative manner as shown at step  325 . These steps could be done only on small number of board locations for spot checking of the material characteristics when a new vendor is selected or can be measured on smaller cards with fewer layers. The smaller card would be used in pre-physical build stage to evaluate the performance of the best material for the target system operation. 
     Such smaller cards could be measured with coaxial probes or with the SMA probes and set-up shown in  FIGS. 12 and 13  where the bandwidth could be typically extended to 50 GHz. 
       FIG. 16  shows a virtual test bench technique  400  that may be used to quantify the performance of a device to the circuit parameter variation, evaluate and virtually reconstruct SPP process, and define the allowable fabrication tolerances in production. As shown in  FIG. 16 , the virtual test bench includes a SPICE simulation technique implementing a programmed computer configured, in one embodiment, as a Virtual Impulse Generator  401  and virtual waveform detector  404 , for simulating inputs pulses  414  and detecting corresponding virtual output pulses  418  of a virtual lossy stripline  410  modeled according to the SPP technique of the invention in the CZ2D solver  415 . That is, the 2-D solver  415  is used to simulate the stripline to obtain line parameter R, L, C, and C as well as α(f). However, the line impedance are affected by the h 1 (mil), h 2 (mil), w (mil), t(mil), ρ(ηΩ.cm), ∈ r,  Z 0 (Ω) parameters as shown in the cross-sectional view of the modeled virtual lossy stripline  410  shown in  FIG. 17 . For example, it is seen that Z 0  variation impacts the SPP predicted α(f). The difference “Δ” between 2-D solver and SPP is defined equation (7): 
     
       
         
           
             
               
                 
                   Δ 
                   = 
                   
                     
                       
                         
                           α 
                           ⁡ 
                           
                             ( 
                             
                               CZ 
                               ⁢ 
                               
                                   
                               
                               ⁢ 
                               2 
                               ⁢ 
                               D 
                             
                             ) 
                           
                         
                         - 
                         
                           α 
                           ⁡ 
                           
                             ( 
                             SPP 
                             ) 
                           
                         
                       
                       
                         α 
                         ⁡ 
                         
                           ( 
                           
                             CZ 
                             ⁢ 
                             
                                 
                             
                             ⁢ 
                             2 
                             ⁢ 
                             D 
                           
                           ) 
                         
                       
                     
                     ⁢ 
                     % 
                   
                 
               
               
                 
                   ( 
                   7 
                   ) 
                 
               
             
           
         
       
     
     Simulations with the virtual test bench technique were made of the effect of process tolerances on the accuracy of the SPP technique. It was found that the technique is able to discern even +/−1.6% changes in characteristics of the transmission lines. 
     The emulated simulation indicates that TDR screening needs to be done prior to the short-pulse excitation. The SPP technique should not be used with lines having more than +/−10% non-uniformity in impedance along the length. In addition, the two lines used, should not differ in Z 0  by more than 5% in order to obtain the SPP predicted attenuation error to be under 10% and this is why step  301  of line screening is needed. 
     The emulation technique can also be used to verifying the accuracy and capability of measurement techniques and so it is of general applicability. The measurement technique described here can also be used to discern effects such as roughness of metallization (see for example, the reference to Alina Deutsch, et al. entitled “Prediction of Losses Caused by Roughness of Metallization in Printed-Circuit Boards”, IEEE Transactions on Advanced Packaging, Vol. 30, No. 2, May 2007, incorporated by reference herein), inhomogeneities in differential transmission line structures due to the fiber weave absence between the lines (see for example, the reference to Alina Deutsch, et al. entitled “Use of the SPP Technique to Account for Inhomogeneities in Differential Printed-Circuit-Board Wiring” Digest of SPI&#39;08, Signal Propagation on Interconnects, May 12-15, 2008, Avignon, France, pp. 22-26, and incorporated by reference herein) and inhomogeneities in top or bottom microstrip structures that have soldermask layers on top of typical insulator layer. In such cases, a two step technique would be used whereby two sets of cards are built. In the first case a homogeneous card or a smooth card or a card without soldermask is built and measured. In the second step the measurement is repeated but on cards with these additional effects included. The technique can also be used to used whereby two sets of cards are built. In the first case a homogeneous card or a smooth card or a card without soldermask is built and measured. In the second step the measurement is repeated but on cards with these additional effects included. The technique can also be used to fully characterize other transmission line structures used in computer systems, such as cables, chip carrier wiring, and on-chip interconnects. 
     SPP is used to generate broadband predictive models for differential lines with different glass-fiber-to-epoxy-resin ratios and also for the soldermask layers used on top and bottom of typical boards. In both cases, a two-step extraction procedure is employed to obtain the broadband complex permittivity for the inhomogeneous structures and correlation with TDT measurements is used to validate the technique. 
     The present invention can be realized as a combination of hardware and software. A typical combination of hardware and software could be a general purpose computer system with a computer program that, when being loaded and executed, controls the computer system such that it carries out the methods described herein. The present invention can also be embedded in a computer program product, which comprises all the features enabling the implementation of the methods described herein, and which, when loaded into a computer system, is able to carry out these methods. 
     Computer program means or computer program in the present context include any expression, in any language, code or notation, of a set of instructions intended to cause a system having an information processing capability to perform a particular function either directly or after conversion to another language, code or notation, and/or reproduction in a different material form. 
     Thus, the invention includes an article of manufacture which comprises a computer usable medium having computer readable program code means embodied therein for causing a function described above. The computer readable program code means in the article of manufacture comprises computer readable program code means for causing a computer to effect the steps of a method of this invention. Similarly, the present invention may be implemented as a computer program product comprising a computer usable medium having computer readable program code means embodied therein for causing a function described above. The computer readable program code means in the computer program product comprising computer readable program code means for causing a computer to affect one or more functions of this invention. Furthermore, the present invention may be implemented as a program storage device readable by machine, tangibly embodying a program of instructions executable by the machine to perform method steps for causing one or more functions of this invention. 
     The system and method of the present disclosure may be implemented and run on a general-purpose computer or computer system. The computer system may be any type of known or will be known systems and may typically include a processor, memory device, a storage device, input/output devices, internal buses, and/or a communications interface for communicating with other computer systems in conjunction with communication hardware and software, etc. 
     More specifically, as shown in  FIG. 18 , a computer system  500 , includes one or more processors or processing units  510 , a system memory  150 , and an address/data bus structure  501  that connects various system components together. For instance, the bus  501  connects the processor  510  to the system memory  550 . The bus  501  can be implemented using any kind of bus structure or combination of bus structures, including a memory bus or memory controller, a peripheral bus, an accelerated graphics port, and a processor or local bus using any of a variety of bus architectures such as ISA bus, an Enhanced ISA (EISA) bus, and a Peripheral Component Interconnects (PCI) bus or like bus device Additionally, the computer system  500  includes one or more monitors  519  and, operator input devices such as a keyboard, and a pointing device (e.g., a “mouse”) for entering commands and information into computer, data storage devices, and implements an operating system such as Linux, various Unix, Macintosh, MS Windows OS, or others. 
     The computing system  500  additionally includes: computer readable media, including a variety of types of volatile and non-volatile media, each of which can be removable or non-removable. For example, system memory  550  includes computer readable media in the form of volatile memory, such as random access memory (RAM), and non-volatile memory, such as read only memory (ROM). The ROM may include an input/output system (BIOS) that contains the basic routines that help to transfer information between elements within computer device  500 , such as during start-up. The RAM component typically contains data and/or program modules in a form that can be quickly accessed by processing unit. Other kinds of computer storage media include a hard disk drive (not shown) for reading from and writing to a non-removable, non-volatile magnetic media, a magnetic disk drive for reading from and writing to a removable, non-volatile magnetic disk (e.g., a “floppy disk”), and an optical disk drive for reading from and/or writing to a removable, non-volatile optical disk such as a CD-ROM, DVD-ROM, or other optical media. Any hard disk drive, magnetic disk drive, and optical disk drive would be connected to the system bus  501  by one or more data media interfaces (not shown). Alternatively, the hard disk drive, magnetic disk drive, and optical disk drive can be connected to the system bus  501  by a SCSI interface (not shown), or other coupling mechanism. Although not shown, the computer  500  can include other types of computer readable media. Generally, the above-identified computer readable media provide non-volatile storage of computer readable instructions, data structures, program modules, and other data for use by computer  500 . For instance, the readable media can store an operating system (O/S), one or more application programs, and/or other program modules and program data for enabling video editing operations via Graphical User Interface (GUI). 
     Input/output interfaces  545  are provided that couple the input devices to the processing unit  510 . More generally, input devices can be coupled to the computer  500  through any kind of interface and bus structures, such as a parallel port, serial port, universal serial bus (USB) port, etc. The computer environment  500  also includes the display device  519  and a video adapter card  535  that couples the display device  519  to the bus  501 . In addition to the display device  519 , the computer environment  100  can include other output peripheral devices, such as speakers (not shown), a printer, etc. I/O interfaces  545  are used to couple these other output devices to the computer  500 . 
     As mentioned, computer system  500  is adapted to operate in a networked environment using logical connections to one or more computers, such as the server device that may include all of the features discussed above with respect to computer device  500 , or some subset thereof. It is understood that any type of network can be used to couple the computer system  500  with a server device, such as a local area network (LAN), or a wide area network (WAN) (such as the Internet). When implemented in a LAN networking environment, the computer  500  connects to local network via a network interface or adapter  529 . When implemented in a WAN networking environment, the computer  500  connects to the WAN via a high speed cable/dsl modem  580  or some other connection means. The cable/dsl modem  180  can be located internal or external to computer  500 , and can be connected to the bus  501  via the I/O interfaces  545  or other appropriate coupling mechanism. Although not illustrated, the computing environment  500  can provide wireless communication functionality for connecting computer  500  with remote computing device, e.g., an application server (e.g., via modulated radio signals, modulated infrared signals, etc.). 
     The terms “computer system” and “computer network” as may be used in the present application may include a variety of combinations of fixed and/or portable computer hardware, software, peripherals, and storage devices. The computer system may include a plurality of individual components that are networked or otherwise linked to perform collaboratively, or may include one or more stand-alone components. The hardware and software components of the computer system of the present application may include and may be included within fixed and portable devices such as desktop, laptop, and server. A module may be a component of a device, software, program, or system that implements some “functionality”, which can be embodied as software, hardware, firmware, electronic circuitry, or etc. 
     In sum, the system and method of the present invention provides an automated or semi-automated technique for large volume testing of PCBs in a production level environment. In such environments, very thick boards are tested with very long plated through-hole (PTH) vias. Testing may be performed on many boards within short time by operators who are not familiar with advanced, delicate measurement technique. 
     While the invention has been particularly shown and described with respect to illustrative and preferred embodiments thereof, it will be understood by those skilled in the art that the foregoing and other changes in form and details may be made therein without departing from the spirit and scope of the invention that should be limited only by the scope of the appended claims.