Abstract:
Systems and methods for employing switched phase shifters and a feed network to provide a low cost multiple beam antenna system for wireless communications. The present systems and methods may also facilitate multi-band communications and employ multi-diversity. The present systems and methods allow communication systems to achieve enhanced performance for communication or other services such as location tracking. The present systems and methods may employ switched phase shifters, multiple diversity antennas and/or a feed network having a multi-layer construction to provide an antenna system with low losses, low external component count and/or which is thin and compact.

Description:
CROSS-REFERENCE TO RELATED APPLICATIONS 
   The present application is a continuation of U.S. patent application Ser. No. 10/720,716, filed Nov. 24, 2003, now U.S. Pat. No. 7,075,485, entitled “LOW COST, MULTI-BEAM, MULTI-BAND AND MULTI-DIVERSITY ANTENNA SYSTEMS AND METHODS FOR WIRELESS COMMUNICATIONS,” the disclosure of which is hereby incorporated by reference herein. The present invention is related to co-pending and commonly assigned U.S. patent application Ser. No. 10/278,062, entitled “DYNAMIC ALLOCATION OF CHANNELS IN A WIRELESS NETWORK”, filed Dec. 16, 2002; Ser. No. 10/274,834, entitled “SYSTEMS AND METHODS FOR MANAGING WIRELESS COMMUNICATIONS USING LINK SPACE INFORMATION”, filed Jan. 2, 2003; Ser. No. 10/348,843, entitled “WIRELESS LOCAL AREA NETWORK TIME DIVISION DUPLEX RELAY SYSTEM WITH HIGH SPEED AUTOMATIC UP-LINK AND DOWN-LINK DETECTION”, filed Jan. 2, 2003; Ser. No. 10/677,418, entitled “SYSTEM AND METHOD FOR PROVIDING MULTIMEDIA WIRELESS MESSAGES ACROSS A BROAD RANGE AND DIVERSITY OF NETWORKS AND USER TERMINAL DISPLAY EQUIPMENT”, filed Oct. 2, 2003; and Ser. No. 10/635,367, entitled “LOCATION POSITIONING IN WIRELESS NETWORKS”, filed Aug. 6, 2003; the disclosures of which are incorporated herein by reference. 

   TECHNICAL FIELD 
   The present invention is generally related to wireless communication systems and specifically related to low cost, multi-beam, multi-band and multi-diversity antenna systems for use in wireless communications. 
   BACKGROUND OF THE INVENTION 
   Typical existing wireless communication antennas capable of providing adaptive beam forming and/or multiple beam switching are relatively expensive. No low cost antenna solution provides multiple beams along with antenna diversity, particularly an antenna that would further provide multiple bands and/or multiple services. Thus, the prior art fails to provide an economical antenna system that has variable beams, reconfigurable for different beam patterns or an economical antenna system that provides communication via multiple bands using multiple services. 
   Gans et al., U.S. Pat. No. 5,610,617, entitled Directive Beam Selectivity for High Speed Wireless Communication Networks, uses butler matrices to form beams for use in wireless communications. The disclosure of Gans is incorporated herein by reference. The antenna of Gans selectively provides a narrow beam in different directions. Thus, using the Gans antenna one may provide a narrow beam to one side or a narrow beam straight ahead. In such existing butler matrices the number of beams are limited by the number of inputs and outputs to the matrix. By way of example, in an existing Butler matrix with four input ports and four output ports, the matrix typically only provides four beams for a user to select from. 
   Existing, so called, adaptive antenna arrays, use components which render the cost of the system very high. Typically in such adaptive antenna arrays, amplifiers and phase shifter circuits are attached to each antenna element, or at least each column of the array. So by way of example, if an existing adaptive antenna array has 64 elements, it may have 64 sets of phase shifters and/or 64 amplifiers/attenuators, or at least one set of phase shifters and/or one set of amplifiers/attenuators for each column of the array. This dramatically increases the cost and complexity of the entire system. These components typically provide an ability to change the magnitude and the phase at each element. Such adaptive antenna arrays require amplifiers and phase shifters to obtain a desired phase and amplitude progression across the array. As phase shifting also induces signal strength losses, amplifiers are also used in an attempt to recoup these losses as well to increase the adaptability of the system. In antenna systems, noise is an important parameter. By using amplifiers at the antenna the noise performance of the adaptive antenna array is also enhanced to also overcome noise created by the phase shifters. An antenna element known in the art is an electromagnetically coupled patch antenna described by R. Q. Lee et. al. in IEEE Transactions on Antennas and propagation, Vol. 38, No. 8, August 1990, the disclosure of which is incorporated herein by reference. 
   BRIEF SUMMARY OF THE INVENTION 
   The present invention is directed to system and method embodiments which employ switched phase shifters and a feed network to provide a low cost manner of achieving multiple beam system for wireless communication systems. Embodiments of the present systems and methods may also facilitate multi-band communications and employ multi-diversity. Such multiple beam, multiple band system and method embodiments allow communication systems to achieve enhanced performance for communication or other services such as location tracking. Embodiments of the present systems and methods may employ switched phase shifters, multiple diversity antennas and/or a feed network having a multi-layer construction to provide an antenna system with low losses, low external component count and/or which is thin and compact. 
   Advantageously, embodiments of the present invention enable multiple beams to be formed simultaneously in different directions in the same frequency band, while providing flexible selection of beam directions, beam widths and beam shapes that can be controlled digitally. The present array is preferably compact and thin, relatively low cost and may operate over multiple bands. Higher band elements may be embedded within lower band elements of an array embodiment, giving similar radiation characteristic on both bands, through both bands sharing the same aperture. A reference-based network may be used, instead of complex Butler matrices, this preferably reduces the number of phase shifter circuits. The phase shifters of embodiments of the present invention have a compact design and may employ a low loss PIN diode network design. The present invention further provides ultra-wideband with greater than twenty percent bandwidth in each band, dual polarization diversity scanning and low manufacturing tolerance for reduced manufacturing cost. 
   The present antenna system can be connected to a wireless communication system such as a wireless LAN or cellular telecommunications network and may be used to enhance performance by appropriately utilizing directional and/or multiple beams. For example, the beams can be utilized to improve coverage in certain directions or for tracking, enhancing location estimation. The beams can also be used to avoid interference in certain directions. Embodiments of the present array can form at least two patterns, simultaneously in some embodiments, that are independent or uncoupled so that diversity may be provided to one or more users, and/or so that multiple users can be serviced. The present systems and methods may employ at least the following components. 
   A variety of different types of antenna elements may be used in the present systems and methods. However, gain, bandwidth, diversity, size and mutual coupling between elements are all considerations for use in the present systems and methods. One suitable element is disclosed in the Lee reference incorporated above. However the present invention may employ novel antenna elements discussed below which are particularly well suited for use by the present systems and methods. Antenna elements of various embodiments of the present invention may employ various beam characteristics, such as forms of diversity including polarization diversity. Thus, elements of embodiments of the present invention may employ multiple branches with two or more feeds that can be used to transmit or receive independent signals with low cross-correlation. Various antenna element configurations and arrangements employed in accordance with embodiments of the present invention allow tighter packing density in an array panel compared to conventional designs. This enable elements to be placed close to each other and still perform in a favorable manner. Also, the bandwidth of the antenna element may be relatively wide in accordance with various embodiments of the present invention, so as to cover the entire spectrum of operation bands for a particular application. 
   Multiple antenna elements with the aforementioned multiple branch wideband configurations are appropriately located and spaced on a supporting structure or panel which may be planar or of other conformal shape to provide an array configuration. The layout of elements on the panel provides room for elements operating at different bands while maintaining low mutual coupling by providing sufficient spacing. The array is preferably laid out to accommodate elements for multiple bands within the same area so that the bands share the same aperture. 
   The phase shifters in embodiments of a shifter network of the present invention are low cost and compact, requiring few external components while providing discrete phases that can be digitally controlled. The present phase shifters may take the form of a very low loss switching circuit. The present systems and methods may employ delay line phase shifts and PIN diodes, varactor diodes or the like, to further reduce loss. The present systems and methods preferably does away with the need for amplitude control through amplifiers, or at least greatly reduces the need for amplitude control, because the phase shifters employed are very low loss and do not contribute any appreciable noise. Elimination of the amplifiers greatly reduces cost of the array and its operation. The discrete phases employed by the present systems and method may, by way of example, be zero, 90, 180, and 270 degrees. 
   The antennas and phase shifters are preferably connected by a feed network that allows multiple beams to be formed in independent directions at multiple frequency bands. The feed network is preferably optimized to reduce coupling between the antennas and phase shifters are optimized to reduce losses, both while being compact. Different methods and systems for feeding the array elements may be used to reduce cross-polarization and to reduce the number of PIN diodes used, resulting in greater cost reductions. 
   The present systems and methods also preferably provide fault detection for malfunctions within the array. This fault detection may employ port detection to facilitate quick diagnostic testing of the array. For example, polling an antenna panel to find out if it is drawing the correct current may be used to detect faulty PIN diodes. 
   The present antenna array preferably enables better performance of the overall wireless communication system. Embodiments of the present systems and methods preferably employ a phase shifter and/or switching approach for beam forming and allows diversity to be easily built into an array. In contrast to typical Butler matrices, not only may the present array be used to provide narrow beams to one side or directly ahead, but also to provide a more omnidirectional pattern or different types of patterns, which may be combinations of narrow beam directions. The number of beams that can be formed in the present array is not dependent on inputs and outputs, and thus is not limited to a predetermined number of beams. Resultantly the present array is much more flexible. 
   The foregoing has outlined rather broadly the features and technical advantages of the present invention in order that the detailed description of the invention that follows may be better understood. Additional features and advantages of the invention will be described hereinafter which form the subject of the claims of the invention. It should be appreciated that the conception and specific embodiment disclosed may be readily utilized as a basis for modifying or designing other structures for carrying out the same purposes of the present invention. It should also be realized that such equivalent constructions do not depart from the invention as set forth in the appended claims. The novel features which are believed to be characteristic of the invention, both as to its organization and method of operation, together with further objects and advantages will be better understood from the following description when considered in connection with the accompanying figures. It is to be expressly understood, however, that each of the figures is provided for the purpose of illustration and description only and is not intended as a definition of the limits of the present invention. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
     For a more complete understanding of the present invention, reference is now made to the following descriptions taken in conjunction with the accompanying drawing, in which: 
       FIG. 1  is a diagrammatic illustration of various beam patterns produced in accordance with at least one embodiment of the present invention; 
       FIG. 2  is a fragmented diagrammatic side view of an a stacked patch antenna element embodiment; 
       FIG. 3  is a fragmented diagrammatic perspective view of an embodiment of the stacked patch antenna of  FIG. 2 ; 
       FIG. 4  is a fragmented diagrammatic perspective view of another embodiment of the stacked patch antenna of  FIG. 2 ; 
       FIG. 5  is a fragmented diagrammatic front view of an embodiment of a multiple branch diversity monopole antenna element in accordance with the present invention; 
       FIG. 6  is a fragmented diagrammatic side view of the antenna element embodiment of  FIG. 5 ; 
       FIG. 7  is a fragmented diagrammatic front view of an alternative embodiment of a multiple branch diversity monopole antenna element in accordance with the present invention; 
       FIG. 8  is a fragmented diagrammatic front view of another alternative embodiment of a multiple branch diversity monopole antenna element in accordance with the present invention; 
       FIG. 9  is a fragmented diagrammatic front view of a third alternative embodiment of a multiple branch diversity monopole antenna element in accordance with the present invention; 
       FIG. 10  is a fragmented diagrammatic front view of an embodiment of an antenna array of multiple tiled multiple branch diversity monopole antenna elements of  FIG. 5 ; 
       FIG. 11  is a fragmented diagrammatic front view of an embodiment of an antenna element providing branch diversity using integrated magnetic and electric dipoles in accordance with the present invention; 
       FIG. 12  is a fragmented diagrammatic front view of an embodiment of an antenna element providing branch diversity using integrated magnetic dipoles and electric monopoles in accordance with the present invention; 
       FIG. 13  is a fragmented diagrammatic front view of an embodiment of an antenna array of antenna elements providing branch diversity using integrated magnetic and electric dipoles of  FIG. 11 ; 
       FIG. 14  is a fragmented diagrammatic front view of an embodiment of an antenna array of antenna elements providing branch diversity using integrated magnetic dipoles and electric monopoles of  FIG. 12 ; 
       FIG. 15  is a diagrammatic illustration of an embodiment of a slot integrated patch antenna element for four branch diversity; 
       FIG. 16  is a diagrammatic illustration of another embodiment of a slot integrated patch antenna element for four branch diversity; 
       FIG. 17  is a diagrammatic illustration of spacing of array elements; 
       FIG. 18  is a diagrammatic illustration of an embodiment of interleaving of array elements for various bandwidths; 
       FIG. 19  is a diagrammatic illustration of another embodiment of interleaving of array elements for various bandwidths; 
       FIG. 20  is a diagrammatic illustration of a third embodiment of interleaving of array elements for various bandwidths; 
       FIG. 21  is a diagrammatic side view of an embodiment of a planer array panel; 
       FIG. 22  is a diagrammatic side view of an embodiment of a curved array panel; 
       FIG. 23  is a diagrammatic top view of an embodiment of a cylindrical array with a front view of an embodiment of a planar panel used to make up the cylindrical array; 
       FIG. 24  is a diagrammatic illustration contrasting the scan angles of a planar array panel and two angularly disposed array panels; 
       FIG. 25  is a diagrammatic side view of an embodiment of a planer array panel employing directors and angled reflectors; 
       FIG. 26  diagrammatically shows an embodiment of element orientation within an array; 
       FIG. 27  diagrammatically shows another embodiment of element orientation within an array; 
       FIG. 28  diagrammatically shows an embodiment of element orientation within an interleaved array; 
       FIG. 29  diagrammatically shows another embodiment of element orientation within an interleaved array; 
       FIG. 30  is a diagrammatic illustration of mutual coupling of an embodiment of square antenna elements in an array; 
       FIG. 31  is a diagrammatic illustration of mutual coupling of an embodiment of cross-type antenna elements in an array; 
       FIG. 32  is a diagrammatic schematic of a feed network in accordance with an embodiment of the present invention; 
       FIG. 33  is a diagrammatic schematic of a feed network in accordance with another embodiment of the present invention; 
       FIG. 34  is a diagrammatic schematic of an embodiment of a single branch phase shifter in accordance with the present invention; 
       FIG. 35  is a diagrammatic schematic of an embodiment of a quad branch phase shifter in accordance with the present invention; 
       FIG. 36  is a diagrammatic schematic of an embodiment of a two branch phase shifter having improved isolation in accordance with the present invention; 
       FIG. 37  is an embodiment of a 45 degree reduced size phase shift line provided in accordance with the present invention; 
       FIG. 38  is another embodiment of a 45 degree reduced size phase shift line provided in accordance with the present invention; 
       FIG. 39A  is an embodiment of a 90 degree reduced size phase shift line provided in accordance with the present invention; 
       FIG. 39B  is an embodiment of a 180 degree reduced size phase shift line provided in accordance with the present invention; 
       FIG. 39C  is an embodiment of a 270 degree reduced size phase shift line provided in accordance with the present invention; 
       FIG. 40A  is a diagrammatic schematic of an embodiment of a two branch phase employing the 90 and 180 degree reduced size phase shift lines of  FIGS. 39A and 39B , in accordance with the present invention; 
       FIG. 40B  is a diagrammatic schematic of an embodiment of an ultra-broadband 90 degree phase shifter having a phase reference line and a phase shifted line; 
       FIG. 40C  is a diagrammatic schematic of an embodiment of an ultra-broadband 180 degree phase shifter having a phase reference line and a phase shifted line; 
       FIG. 41  is a diagrammatic schematic of an embodiment of a quad branch phase shifter employing the 90, 180, and 270 degree reduced size phase shift lines of  FIGS. 39A ,  39 B and  39 C, in accordance with the present invention; 
       FIG. 42  is a diagrammatic schematic of a two branch feed network in accordance with an embodiment of the present invention; 
       FIG. 43  is a diagrammatic schematic of a phase shift feed embodiment having a phase shifter and a switch in accordance with the present invention; 
       FIG. 44  is a diagrammatic illustration showing differential feed of spaced antenna elements in accordance with another embodiment of the present invention; 
       FIG. 45  is a diagrammatic illustration of an array element arrangement embodiment, without differential feed, shown with a resultant antenna beam pattern and cross-polarization power reduction; 
       FIG. 46  is a diagrammatic illustration of an array element arrangement embodiment employing differential feed, shown with a resultant antenna beam pattern and cross-polarization power reduction; 
       FIG. 47  is a diagrammatic illustration of another array element arrangement embodiment employing differential feed, shown with a resultant antenna beam pattern and cross-polarization power reduction; and 
       FIG. 48  is a diagrammatic illustration of a third array element arrangement embodiment employing differential feed, shown with a resultant antenna beam pattern and cross-polarization power reduction. 
   

   DETAILED DESCRIPTION 
   Various embodiments of the present systems and method may be used to form multiple beams simultaneously in different directions and/or with different attributes or characteristics, such as beam width, polarizations, or the like, using low cost panels. Embodiments of the present systems and methods provide different manners for reducing costs and providing solutions by varying the feed network employed. The present systems and methods may make use of inexpensive PIN or varactor diodes while maintaining performance and operating in multiple bands. In accordance with embodiments of the present systems and methods an array can employ closely packed, interleaved elements without sacrificing the radiation pattern resulting in a thin, compact array. The array may be further reduced in size through the use of switched phase shifters, eliminating the need for a bulky butler matrix. Multiple operating bands having the same aperture may result from interleaving elements for the various bands on a panel. The bandwidth of an array of the present invention may also be very broad. For example, a full gigahertz of bandwidth coverage may be provided at the high band in an array of the present invention. Digitized scanning capability is provided by panel embodiments, particularly those employing embodiments of the stacked patch element configurations. The array panels of the present invention are very broadband so manufacturing tolerances are generous, as slight variations will not greatly affect the bandwidth, or affect the bands of operation. 
     FIG. 1  is an illustration of various beam patterns  101  through  112  produced in accordance with embodiments of the present systems and methods. Digital selection of phase shifts allows selection of these, or similar beam patterns. As will be appreciated by one of ordinary skill in the art the various beams have useful properties. For example, patterns  101 ,  105 , and  106  can be used for beam scanning. Pattern  102  provides a broad beam for providing good coverage throughout a service area. 
   Embodiments of the present invention preferably employ antenna elements that have multiple antennas integrated therein. These elements may be generally referred to as having multi-branch diversity or referred more specifically to as having two, three or four branch diversity, or the like. Antenna elements and arrays provided in accordance with the present invention are shown on  FIGS. 2 through 20  and are described below. 
     FIG. 2  is a diagrammatic side view of an a stacked patch antenna element configuration  200  disposed within a panel, between panel covers  201  and  202 .  FIGS. 3 and 4  are diagrammatic perspective views of embodiments  300  and  400  of stacked patch antenna  200  of  FIG. 2 . Antenna element  200  may be tuned by using parasitic element  203 , spaced apart from feed element  204  at a predetermined height to provide higher gain, broaden the response band of element  200 , and provide polarization purity. The height that parasitic element  203  is spaced above feed element  204  is preferably tuned to give a very broadband match. Preferably feed element  204  and the associated feed network are disposed on and/or embedded within the same Printed Circuit Board (PCB) structure  205  or the like. RF circuits and feed via  206  on the backside of feed antenna  204  are shielded by feed antenna ground plane  207 , reducing cross-polarization and side lobe contribution. Feed of antenna element  200  may be simplified by avoiding soldering joints through integration of the feed network and at least a portion of the elements on PCB  205 . Integrated feed via  206  on feed antenna is employed rather than an aperture feed mechanism to reduce backlobe radiation. Further backlobe radiation can be reduced by ground plane  208  placed at a distance from RF feed circuitry  209  on an underside of PCB  205 . In accordance with embodiments of the present invention, each element  200  in an array may have at least two feeds (second feed not shown) to provide dual branch diversity. The feeds are isolated sufficiently to produce sufficient diversity advantages. In accordance with embodiments of the present invention elements can have any number of feeds for providing diversity. 
   The “cross-style” antenna element  300  of  FIG. 3  may be used to reduce mutual couplings. Parasite antenna element  303  is approximately 1.3 times larger than feed antenna  304  to generate good dual resonance. Parasite antenna dimensions are approximately 0.29 wavelengths (λ) square in size with respect to a lowest operating frequency for antenna element  300 . Parasitic element  303  is preferably spaced about 0.05λ to about 0.08λ from feed element  304  to optimize broadband behavior for good degenerated modes. With parasitic element  303  positioned at an over coupled location above feed element  304 , stacked patch antenna element configuration  300  gives an increase in bandwidth on the order of 17 percent greater than that of the feed element alone. 
   Antenna element  400  of  FIG. 4  has parasitic element  403  optimized to similar size as feed antenna  404  such as may be suggested by space constraints. Parasite antenna element is approximately 0.2λ square in size with respect to a lowest operating frequency for antenna element  400 . Broadband behavior is optimized through the height of parasitic antenna element  403 , disposed about 0.04 to 0.06λ above feed element  404  for good degenerated modes Parasite antenna  403  is not cross-shaped, and thereby provides increased bandwidth on the order of 26 percent greater than that of the feed element alone. 
   Multiple branch diversity monopole element embodiment  500  is shown in  FIG. 5 . A side view of embodiment  500  is shown in  FIG. 6 . Alternative, embodiments  700 ,  800  and  900  of multiple branch diversity monopole antenna elements are shown in  FIGS. 7 ,  8  and  9 , respectively. Antenna element  500  employs monopoles  501  as feed elements. Monopoles  501  may be a dielectric loaded ceramic antenna element, or the like. Ground plane  502  forms a differential path for monopoles  501 , resulting in dipole like characteristics for element  500 . Ground plane  502  preferably supports feed network  503  and phase shifting circuitry (not shown) discussed below. Feed network  503  feeding a signal to monopoles  501  may take the form of microstrip lines defined on a dielectric (not shown) with ground plane  502  disposed on an opposite surface. Alternatively, monopoles  501  may be feed by a planar waveguide or the like used to guide the signal into the antenna elements. Use of microstrips or planar waveguides in the feed network facilitate providing a generally planer array. Monopoles  501 , feed network  503  and ground plane  502  are preferably placed before reflector  504  at an optimum distance of Rλ, which may be about 0.25λ. Reflector  504  is also a ground plane. Since feed elements  501  can be dielectric loaded monopoles they can be small in size. Thus a small array can be implemented in accordance with embodiments  500 ,  700 ,  800  and  900 . Planar disc monopole  701  may be utilized by embodiment  700  for ultra wideband characteristics. Multiple circular ring monopoles  801  may be used to provide antenna element  800  multi-band characteristics. Square plate monopoles  901  may be employed to provide antenna element  900  broadband characteristics. Square plate monopole  901  with shorting pins (not shown) at the corners to ground plane  502  may be used to generate additional lower order mode and broadband characteristics. Various configurations of embodiments  500 ,  700 ,  800  and  900  may be extended into an array to provide a multiple branch diversity antenna system. The three monopoles ( 501 ) of antenna element  500  may be fed to provide slant left, slant right and vertical polarization, whereas the two monopoles of elements  700 ,  800  and  900  (monopoles  701 ,  801  and  901 , respectively) may be fed to provide slant left and slant right polarizations. However, embodiments of elements  500 ,  700 ,  800  and  900  may employ fewer or more monopoles  501 ,  701 ,  801  or  901  than shown to provide various polarizations. 
   Multiple ones of element  500  can be tiled into an array, such as array  1000  of  FIG. 10 . Four elements ( 500 ) are shown in  FIG. 10  but any number of elements may be tiled into an array, as indicated by the ellipses to the right and below the illustrated elements. Elements  500  may be spaced appropriately for providing phased array beam forming as desired, such as spaced one-half a wavelength from each other. That will provide an ability to produce a number of independent beams with various independent characteristics including polarity diversity, various widths, various angles and the like from the array. Elements  500  are preferably supported by feed network  1001 , which may be similar to feed network  503  described above. 
     FIGS. 11 and 12  show diagrammatic illustrations of embodiments of slot integrated patch antenna elements  1100  and  1200  for four branch diversity. The slot integrated patch antenna elements  1100  and  1200  have X-shaped slot  1101  or  1201  cut in electric conductor  1102  or  1202 , to provide a slot antenna element while electric conductor  1102  or  1202  forms a patch antenna element. With attention directed specifically to  FIG. 11 , patch feeds  1103  and  1104  for slot integrated patch antenna element  1100  may be placed generally aligned with intersection  1105  of X-shaped slot  1101 . The slot feeds for slot integrated patch antenna element  1100  are shown by arrows  1108  and  1109 . Turning now to  FIG. 12 , patch feeds  1203  and  1204  for slot integrated patch antenna element  1200  may be placed generally aligned with each slot  1206  and  1207  of X-shaped slot  1201 . The slot feeds for slot integrated patch antenna elements  1200  are shown by arrows  1208  and  1209 . In each embodiment of slot integrated patch antenna elements  1100  and  1200 , feeds  1103 , and  1104  or  1203  or  1204 , respectively provide two branch diversity through orthogonal polarizations. Slots  1106  and  1107  or  1206  or  1207  defined in electric conductor  1102  or  1202  provide magnetic fields, resulting in two orthogonal beam branches for each of the two original beam diversity branches thus providing four branch (or beam) diversity. Elements  1100  or  1200  can be tiled in an array. In such an array, each feed to the antenna can be controlled to form various scanning beams. 
     FIGS. 13 and 14  illustrate antenna elements  1300  and  1400  providing branch diversity using integrated magnetic and electric dipoles. Magnetic dual branch diversity antenna  1301  or  1401  is provided by slots  1302  and  1303  or  1402  and  1403  in the electrical conductor boundary  1304  or  1404 . Elements  1300  and  1400  are fed close to an edge of one end of slots  1302 ,  1303 ,  1402  or  1403  as shown by the arrows in  FIGS. 13 and 14 . With attention directed to  FIG. 13 , four beams providing four branch diversity may be obtained by integrating magnetic slot antenna  1301  with cross shaped electric dipoles  1305  within the same area. Alternatively, as shown in  FIG. 14 , four beams providing four branch diversity may be obtained by integrating magnetic slot antenna  1401  with respective electric monopole  1405 , using a bottom feed. Element  1400  may use an electric monopole element that is half the length of that used by element  1300 , saving, space and weight. Since the E-field and the B-fields of grounded material  1304  or  1404  have differently polarized beams diversity is achieved between the beams produced by the magnetic dipoles and the electric dipoles of an element ( 1300  or  1400 ). Further, the beam patterns generated by magnetic antennas  1301  or  1401  will differ from the beam patterns generated by electric dipoles  1305  or  1405 , providing further diversity. 
   As shown in  FIGS. 15 and 16  respectively, the antenna elements  1300  or  1400  may be tiled to form an antenna array providing four branch diversity systems  1500  and  1600 . Preferably, a reflector plane  1501  or  1601 , or the like, is used in arrays  1500  and  1600  to make direct the beams, particularly as the beams provided by elements  1300  or  1400  may be somewhat omnidirectional. Reflector plane  1501  or  1601  is preferably placed an optimum distance, Rλ, from the plane of antenna elements  1300  and  1400 . 
   As generally illustrated in  FIG. 17 , spacing of array  1700  elements  1701  in ΔY and ΔX is preferably optimized for scanning angle and gain in accordance with aspects of the present invention. For example ΔX may primarily be optimized for optimum +/−45 degree scan angles to approximately 0.43λ spacing and to provide optimum gain in those directions. However, larger ΔX or ΔY spacing may provide higher gain. Thus, as a further example, ΔY may be optimized primarily to improve gain of the array, but scan angle may be limited if ΔX or ΔY spacing is too large. 
     FIGS. 18 and 19  depict arrays  1800  and  1900  employing aperture sharing in accordance with the present invention. However, inter-element orientations for dual band array variations  1800  and  1900  provide independent radiation pattern characteristics on bands for elements  1801  and  1802  or  1901  and  1902 , respectively. With attention directed specifically to  FIG. 18  larger patches  1801  represent lower frequency elements and smaller patches  1802  represent higher frequency elements. Array  1800  employs five low frequency elements  1801 , and within the space occupied by these five low frequency elements higher frequency elements  1802  are tiled or interspersed such that all of elements  1801  and  1802  are sharing the same aperture, possibly employing different radiation patterns. Similarly, in  FIG. 19  cross-shaped antenna elements  1901  have smaller higher frequency elements  1902  embedded within their cross-shapes such that all of elements  1901  and  1902  are sharing the same aperture, possibly employing different radiation patterns. 
     FIG. 20  depicts an embodiment of array  2000  providing aperture sharing with an ability to have similar radiation pattern characteristics on both bands. In the illustrated embodiment of array  2000  four larger low frequency elements  2001  are disposed along two outside edges of the array, and smaller high frequency elements  2002  are disposed within/between the two rows of low frequency elements  2001 . In dual band array  2000  with, for example, a frequency ratio of approximately 2:1 between the bands, an optimal ΔY spacing of approximately 0.65λ may be utilized for both higher and lower frequency elements if spacing of the lower frequency band elements provides sufficient spacing. 
   As depicted in  FIGS. 21 ,  22  and  23  arrays  2100 ,  2200  or  2300  may be implemented on a flat structure ( 2100 ), on a curved structure ( 2200 ), or in a cylindrical structure ( 2300 ) in accordance with the present invention. This may be accomplished by referencing elements on a planar, curved or cylindrical surface or as shown in  FIGS. 22 and 23 , array panels  2201  or  2301  can be used to form a curved array  2200  or a cylindrical array  2300 . Likewise spherical arrays could also be formed using array panels. Beam characteristics and direction may be determined by switching RF signals to various ones of array panels. Curved surfaces of arrays  2200  and  2300  preferably increase the scan angle of the whole array. Alternatively, the scan angle of an array panel may be increased by using a star topology feed network, such as by distributing an RF feed at the center of an array structure to output nodes which are situated around this center. Through use of a star topology feed network the array panels may be laid out in a generally cylindrical manner to provide a cylindrical array that scans 360 degrees. Each panel may also employ individual phase shifters within diversity branch feeds to provide further up-tilt or down-tilt beams. As one of ordinary skill in the art will appreciate an array may be disposed on surfaces of any number of shapes including, by way of example, the faces of spherical or hemispherical structures. 
   As shown by the beam patterns depicted in  FIG. 24  angularly disposed array faces  2400 , similar to the faces illustrated in  FIG. 23  for cylindrical array  2300 , may enhance scan angle of an array, see the increased scan angle depicted by arc  2403 . Thus, to reduce the number of elements necessary for an array, panels  2401  may be implemented in a triangular arrangement to increase the scan angle compared to a single planar array  2402 . Each panel  2401  may have various column and rows of elements  2404 . The angle of disposition of the array faces, α, may determine the maximum scan angle or field of view for an array. 
   The scanning angle of an array may be extended by using array configuration  2500 , diagrammatically shown in  FIG. 25 . Conventionally, radiation along the plane of an array is a null field. However, in accordance with the present invention, radiation characteristics towards this plane may be increased. When scanning toward an angle along the face of array  2501 , see arrow  2502 , resonant structures  2503 , for example dipole elements, may be used to act as directors to guide fields toward such an acute angle. Structures  2503  may be passive or active. A feed network will provide relevant signals to active structures, but not to passive structures. Dielectric PCB  2504  supporting antenna elements  2506  preferably extends to support directors  2503 . However, ground plane  2505 , as may be present to support field performance of patch antenna elements  2506 , preferably does not extend beyond patch elements  2506  to director structures  2503 . Resultantly, ground plane  2505  may form a reflector for the directors, to aid in steering beams generally along the plane of the antenna array. This would provide an edge-fired or end-fired antenna array. Additionally or alternatively, angular reflector plates  2507  may be placed at a position such as at the termination of the ground plane  2505 , to provide higher gain of the edge-fired or end-fired antenna array. Reflector plates  2507  may also serve to optimize and tuned beam widths of the array panel formed by elements  2506  and  2503 . A preferred angle of the reflector plate for maximal gain may be 45 degrees relative to the plane of the PCB  2504  and the preferred length of reflector plates  2507  may be about 0.25λ. 
   As shown in  FIGS. 26 and 27  element orientation within arrays  2600  and  2700  may vary between arrays. Each of configurations  2600  and  2700  provides dual branch diversity. In array  2600  of  FIG. 26  with “upright” oriented patch arrangement of cross elements  2601 , the edge to edge spacing between the elements will be closer than in array  2700 , such as at 0.13λ to provide desired 0.5λ element to element spacing. However, array  2700  of  FIG. 27  may result in a smaller array while providing the desired 0.5λ spacing. Preferably, at 0.5% inter element spacing, edge to edge distance between elements is also relaxed, such as to 0.2λ. Inter-element spacing in array  2700  may be reduced due to reductions in mutual coupling of cross shaped antenna elements  2701  (discussed below in relation to  FIG. 31 ), without severe performance degradation. Further, the configuration of array  2700  may avoid unbalanced mutual coupling, thus avoiding different radiation patterns between branches. Finally, 45 degree slant right and slant left polarizations provided by array  2700  may provide better diversity performance in some situations. 
   Turning to  FIGS. 28 and 29 , interleaved arrays  2800  and  2900  are shown. As shown in  FIG. 28 , larger lower frequency cross-shaped elements  2801  can be rotated to relax spacing requirements of embedded higher frequency elements  2802  in contrast to the spacing of elements  2901  and  2902  in array  2900  of  FIG. 29 . Rotated elements  2801  and  2802  may also provide greater isolation between the different band elements. Additionally, radiation pattern characteristics of array  2900  may not be as desirable as the radiation characteristics of array  2800  in some circumstances. 
     FIGS. 30 and 31  illustrate mutual coupling between closely placed patch antenna elements.  FIG. 30  shows the strong mutual coupling  3001  of square patch antenna elements  3002  while  FIG. 31  shows the relatively weak mutual coupling  3101  between rotated cross-shaped antenna elements  3102 . Thus, cross-shaped elements reduce mutual coupling between elements as shown in  FIG. 31 , while allowing more space for upper band elements, as shown in  FIG. 28 , without sacrificing performance, achieving relatively high gains with symmetrical beam patterns. Further, use of cross-shaped elements reduce antenna element size due to longer effective current paths, resulting in better mutual coupling characteristics while allowing smaller arrays to be provided. 
   The present systems and methods may employ at least a dual band scanning array with at least dual beams in each band. Preferably, each beam is independently controlled with its respective phase shifting circuits. Alternatively, dual beams of the same band shares a similar set of phase shifting circuits. The present invention may employ a phase shifter network employing discrete phase shifts, such as zero, 90, 180 and 270 degrees phase shifts. However, the present invention is not limited to these particular discrete phase shifts and may alternatively employ other fixed phase shifts or continuous variation phase shifts.  FIG. 32  is a simplified diagrammatic illustration of an embodiment of phase shifter deployment  3200  with four antennas of an array. In  FIG. 32  one phase shifter  3201  is deployed in conjunction with each antenna element  3202 . Preferably, a phase shifter is attached to each branch of the associated antenna element. Wilkinson power dividers or the like (not shown) may be used for isolation. The present invention preferably provides a dual band scanning array with at least dual beams in each band. Each beam may be independently controlled through its respective element&#39;s or elements&#39; phase shifting circuits. Alternatively, dual beams of the same band may share a similar set of phase shifting circuits using a switch to switch between two antenna feeds. Also, to reduce the number of components, such as phase shifters and/or PIN diodes, used in an array the phase shifter arrangement shown in  FIG. 33  may be employed in accordance with the present invention. In the layout embodiment illustrated in  FIG. 33  one phase shifters  3301  is associated with each of three antenna elements  3302  of a branch, with fourth element  3303  providing an unshifted reference phase. 
     FIGS. 34 and 36  show shifters that may be employed by the present invention in a true delay line phase shifter network.  FIG. 34  shows a simplified schematic of single branch phase shifter  3400 ,  FIG. 35  shows a simplified schematic of quad branch phase shifter  3500 , and  FIG. 36  shows embodiment of two branch phase shifter  3600  having improved isolation. The embodiment of single branch phase shifter  3400  shown in  FIG. 34  uses two PIN diodes  3401  and  3402 , in an opposite back-to-back configuration, to ensure isolation between input port  3403  and the output port  3404 , inductor  3405  provides a Direct Current (DC) bias in the length ΔΦ. Length ΔΦ may be used to determines the amount of phase provided by phase shifter  3400 . Diodes  3401  and  3402  give good isolation when bias is off. When bias on, diodes  3401  and  3402  facilitate good transmission characteristics. 
   In delay phase shifter  3500  of  FIG. 35  meander line inductors  3501 ,  3502 ,  3503  and  3504  are used. Meander line inductors are similar to printed circuit transmission lines, but are very high in impedance. The line length of the meander line inductors  3501 ,  3502 ,  3503  and  3504  is preferably about 0.25λ g  (guided wavelength), so as to provide very high impedance at the end where it feeds to an RF line. That reduces the amount of losses on the RF lines. Four different line lengths, ΔΦs  3505 ,  3506 ,  3507  and  3508 , in phase shifter  3500  provide four discrete phase shifts, preferably based around reference line length of zero phase shift line  3505 . The illustrated embodiment of  FIG. 35  is shown as calibrated to zero, 90, 180, and 270 degrees. Preferably, each line of phase shifter  3500  is isolated with back to back diodes  3510 . When bias is provided to a particular branch, the PIN diodes in either direction are forward biased. However, the PIN diodes of the other branches, which are not meant to turn on, are reverse biased. This provides a very good isolation for the entire phase shifter system. Additional diode  3520  may be placed in 90 degree line  3506  to further ensure isolation. Second additional diode  3530  may be placed in 270 degree line  3508  at a distance of 0.25λ g  from junction diodes  3535  to further insure isolation by providing an open short circuit at 0.25λ g  from junction  3535 . 
   As shown in  FIG. 36 , for the ΔΦ line length calibrated to zero degrees ( 3605 ), a line length of 0.25λ g  may provide superior junction isolation, in which case additional diode  3620  placed in 90 degree line  3606  may alternatively be placed 0.25λ g  from junction  3535  to provide better junction isolation. Further implementation of additional diodes on different ΔΦ lengths at intervals of 0.25λ g  from junctions may be employed to further enhance junction isolation and reduce noise in a delay phase shifter, such as delay phase shifter  3500 . When such diodes are biased on they provide another open circuit toward the junction side, providing better isolation and very broad band behavior. These additional diodes preferably prevent opposite phased power leakage cancellation between different branches and broaden operational bandwidth by canceling resonance effects in transmission paths. Resultantly transmission losses are also generally reduced throughout the entire phase shifter network. The phase shifter embodiment of  FIG. 35 , particularly enhanced with additional diodes as demonstrated in  FIG. 36  enables use of inexpensive, somewhat lossy diodes while providing reasonable performance at higher frequencies. 
   Transmission lines in phase shifters, such as those for 180 and 270 degree phase shifts in phase shifter  3500  of  FIG. 35 , can be quite long resulting in a large phase shift network.  FIGS. 37 ,  38  and  39 A illustrate a manner of reducing the phase path lengths, the physical length of the transmission lines, into very small equivalent circuits. As is known in the art and shown in  FIG. 37  a 45 degree line can be reduced in size using three stubs  3701  to form reduced size phase shift line  3700 . This reduced size phase shift line  3700  can be reshaped to provide reduced size 45 degree phase shift line  3800 . Sections of these lines can be used to form various reduced sized switch line phase delay circuit. For example, two reduced size 45 degree phase shift lines  3800  can be combined and provided proper impedances to provide a reduced size 90 degree phase shift line  3900  of  FIG. 39A . Stub impedances may be tuned for 50Ω end to end, by way of example. Four reduced size 45 degree phase shift lines  3800  may be combined to provide 180 degree reduced size phase shift line  3910  of  FIG. 39B , and six reduced size 45 degree phase shift lines  3800  may be combined to provide 270 degree reduced size phase shift line  3920  of  FIG. 39C . 
   Sections of reduced size phase shift lines  3800 ,  3900 ,  3910  and  3920  may be used to form various reduced sized switch line phase delay circuits, such as circuits  4000  and  4100  shown in  FIGS. 40 and 41 . Phase shifter circuit  4000  of  FIG. 40A  is made up of two phase shifters  4001  and  4002 . Phase shifter  4001  has two branches, zero degree branch  4003  and 90 degree branch  4004 . Zero degree branch  4003  does not make use of a reduced size phase shift line, whereas 90 degree branch  4004  employs two 45 degree reduced size phase shift lines ( 3800 ) to provide a 90 degree phase shift line similar to line  3900  described above. Phase shifter  4002  also has two branches, branch  4005  is a zero degree branch and branch  4006  is a 180 degree branch. As with phase shifter  4001  zero degree branch  4005  does not make use of a reduced size phase shift line. 180 degree branch  4006  employs four 45 degree reduced size phase shift lines ( 3800 ) to provide a 180 degree phase shift line similar to line  3910  described above. Phase shift network  4001  may provide phase shifts for zero, 90, 180 or 270 degrees.  FIG. 41  shows reduced circuitry  4100  for a phase shifter, such as phase shifter  3500  of  FIG. 35 . 
   As is known in the art and shown in  FIG. 40B  an ultra-broadband 90 degree phase shifter circuit  4010 , such as with a frequency ratio greater than two-to-one, may comprise a phase reference line  4012  which has a guided wavelength length corresponding to a phase length of 270 degrees and phase shifted line  4013  providing a 90 degrees broadband phase shift with respect to reference line  4012 . Phase shifted line  4013  may comprise two orthogonal stubs  4015  and  4016  forming a “plus-sign shape” with one end  4018  of “vertical” stub  4015  shorted to ground by shorting pins  4017  while the other end ( 4019 ) is an open circuit. Preferably, by designing circuit  4010  at a center frequency of interest, for example 5.5 GHz, circuit  4010  may operate within +/−5 degrees of a 90 degrees phase shift such as to 3.3 GHz. As shown in  FIG. 40C , a present inventive ultra-broadband 180 degree phase shifter circuit  4020  may comprise a phase reference line  4022  which has a guided wavelength length corresponding to a phase shift of 540 degrees and cascaded phase shifted line  4023  providing a 180 degrees broadband phase shift with respect to reference line  4022 . Similarly, other inventive broadband phase shifters, such as a 270 degree broadband phase shifter, may be provided using a cascaded guided wavelength length reference line and corresponding cascaded phase shifted lines. Alternatively, reference phase lines  4012 ,  4022 , or the like may be meandered to further reduce module size. 
     FIG. 42  discloses feed network elements deployed in accordance with the present invention. Feed network  4200  shown in  FIG. 42  is preferably disposed in array panels. Feed network  4200  employs dual branch interlaced feed for space optimization and can be implemented on microstrip lines, embedded striplines or the like on a PCB such as PCB  205 / 2504  discussed above. The illustrated embodiment of feed network  4200  shown in FIG.  42  has two RF feed branches,  4201  and  4202 , integrated for a single or multi-band, dual branch array. Each RF feed, by way of example, feeds four groups of antenna elements, or columns. RF branch  4201  feeds antenna elements or columns  4203 - 4206 , and RF branch  4202  feeds antenna elements or columns  4207 - 4210 . Antennas or columns  4203 - 4205  and  4207 - 4209  each have associated phase shifters  4213 - 4215  and  4217 - 4219 , respectively, with antenna elements or columns  4206  and  4210  acting as reference elements, without phase shifters. 
   However, the number of phase shifters used in a feed network, such as feed network  4200 , may be reduced through the use of phase shifters and branching out the signal using a switch by implementing dual branch feed  4300 , as shown in  FIG. 43 . Feed  4300  may be used to reduce a four branch delay line phase shifter network to a two branch and one switch network. Feed  4300  may reduce the number of PIN diodes and phase shifter components employed in a feed network of the present invention by 30 percent or more. Input at  4301  is feed to a zero or 90 degree phase shifter  4302 , such as phase shifter  4001  described above. The output of phase shifter  4302  is feed through switch  4303  where the signal is switched to either zero phase inputs  4304  of antenna elements  4305  and  4306 , or 180 degree phase inputs  4307  of antenna elements  4305  and  4306 , via divider  4308  or  4309  to obtain desired phase shifts. In combination phase shifter  4302  and switch  4303  complete a phase shift system of zero, 90, 180 and 270 degrees and alleviates the need for one set of phase shifters in a branch. Further, feed  4300  avoids possible signal cancellation resulting from over 180 degrees shifts within a phase shifter. Other embodiments of a feed network employing phase shifters and switched branch feeding to reduce component counts, while achieving desired phase shift performance, are also possible. For example, phase shifter  4302  may be configured so as to provide 0 degree and 270 degree phase shifts, and feed lines of zero phase input ports  4304  of elements  4305  and  4306  may be extended by a length sufficient to provide an additional 90 degrees of phase shift. 
   Differential feed  4400  may be used to limit cross-polarization power reduction through the use of opposite phase feed on antenna elements  4401  and  4402 , as shown in the illustrated embodiment of  FIG. 44 . Feeds  4403  and  4404  to antenna elements  4401  and  4402 , on opposite sides of the elements, which may be spaced half a wavelength apart, can be feed to provide a signal to the element 180 degrees out of phase. However, the overall field vector of the resultant beam remains in-phase. As shown in  FIGS. 46 through 48 , subarray differential feed control may be used to take advantage of differential feed placement in arrays to limit cross-polarization power reduction. However, first turning to  FIG. 45 , array  4500  which does not employ differential feed exhibits a radiation pattern with cross-polarization  4510  of minus 18 dB down from main beam  4520 . In  FIG. 46  antenna element group  4601  and  4602  of array  4600  form the equivalent of phase cancellation for cross-polarization in array  4600  using differential feed to reduce cross-polarization power reduction. Radiation pattern  4610  is minus 30 dB down from main beam  4620 . In  FIG. 47 , group  4701  of middle elements of array  4700 , which have a half wavelength space from feeds of adjacent elements  4703 - 4706  give about minus 30 dB of cross-polarization isolation between radiation pattern  4710  and main beam  4720 . In  FIG. 48  antenna element group  4801  and  4802  of array  4800  are disposed with opposite facing feeds to provide differential feed to reduce cross-polarization power reduction. Radiation pattern  4810  is minus 30 dB down from main beam  4820 . 
   A control system for the present inventive antenna array may employ current sensing for fault detection. Preferably, circuitry for such fault sensing is embedded in the feed network to automatically assess total current drawn by an array panel. This circuitry may assesses the total current drawn by the phase shift network. Phase shifts may be randomly activated, or activated in predetermined patterns, to assess if the current drawn by a panel or particular circuitry in a panel, is within acceptable/expected levels. Such testing may be used to determine if diodes in the phase shifters are operational. Preferably, functionality is provided to enable a network administrator to poll an array panel, such as via network management system, to assess if a panel is faulty 
   Although the present invention and its advantages have been described in detail, it should be understood that various changes, substitutions and alterations can be made herein without departing from the invention as defined by the appended claims. Moreover, the scope of the present application is not intended to be limited to the particular embodiments of the process, machine, manufacture, composition of matter, means, methods and steps described in the specification. As one will readily appreciate from the disclosure, processes, machines, manufacture, compositions of matter, means, methods, or steps, presently existing or later to be developed that perform substantially the same function or achieve substantially the same result as the corresponding embodiments described herein may be utilized. Accordingly, the appended claims are intended to include within their scope such processes, machines, manufacture, compositions of matter, means, methods, or steps.