Abstract:
An electronic filter includes a substrate, a ground conductor, an input, an output, a first microstrip line positioned on the substrate and electrically coupled to the input and the output, and a first tunable dielectric varactor electrically connected between the microstrip line and the ground conductor. The input preferably includes a second microstrip line positioned on the substrate and including a portion lying parallel to the first microstrip line. The output preferable includes a third microstrip line positioned on the substrate and including a portion lying parallel to the first microstrip line. The first microstrip line includes a first end and a second end, the first end being open circuited and the varactor being connected between the second end and the ground conductor. The filter further includes a bias voltage circuit including a high impedance line, a radial stub extending from the high impedance line, and a patch connected to the high impedance line for connection to a DC source. In a multiple pole embodiment, the filter further includes additional microstrip lines positioned on the filter substrate parallel to the first microstrip line and additional tunable dielectric varactors electrically connected between the additional microstrip lines and the ground conductor.

Description:
CROSS REFERENCE TO RELATED APPLICATION 
     This application claims the benefit of the filing date of U.S. Provisional Application No. 60/163,498, filed Nov. 4, 1999. 
    
    
     FIELD OF INVENTION 
     The present invention relates generally to electronic filters, and more particularly, to tunable filters that operate at microwave frequencies at room temperature. 
     BACKGROUND OF INVENTION 
     Electrically tunable microwave filters have many applications in microwave systems. These applications include local multipoint distribution service (LMDS), personal communication systems (PCS), frequency hopping radio, satellite communications, and radar systems. There are three main kinds of microwave tunable filters, mechanically, magnetically, and electrically tunable filters. Mechanically tunable filters are usually tuned manually or by using a motor. They suffer from slow tuning speed and large size. A typical magnetically tunable filter is the YIG (Yttrium-Iron-Garnet) filter, which is perhaps the most popular tunable microwave filter, because of its multioctave tuning range, and high selectivity. However, YIG filters have low tuning speed, complex structure, and complex control circuits, and are expensive. 
     One electronically tunable filter is the diode varactor-tuned filter, which has a high tuning speed, a simple structure, a simple control circuit, and low cost. Since the diode varactor is basically a semiconductor diode, diode varactor-tuned filters can be used in monolithic microwave integrated circuits (MMIC) or microwave integrated circuits. The performance of varactors is defined by the capacitance ratio, C max /C min , frequency range, and figure of merit, or Q factor at the specified frequency range. The Q factors for semiconductor varactors for frequencies up to 2 GHz are usually very good. However, at frequencies above 2 GHz, the Q factors of these varactors degrade rapidly. 
     Since the Q factor of semiconductor diode varactors is low at high frequencies (for example, &lt;20 at 20 GHz ), the insertion loss of diode varactor-tuned filters is very high, especially at high frequencies (&gt;5 GHz ). Another problem associated with diode varactor-tuned filters is their low power handling capability. Since diode varactors are nonlinear devices, larger signals generate harmonics and subharmonics. 
     Varactors that utilize a thin film ferroelectric ceramic as a voltage tunable element in combination with a superconducting element have been described. For example, U.S. Pat. No. 5,640,042 discloses a thin film ferroelectric varactor having a carrier substrate layer, a high temperature superconducting layer deposited on the substrate, a thin film dielectric deposited on the metallic layer, and a plurality of metallic conductive means disposed on the thin film dielectric, which are placed in electrical contact with RF transmission lines in tuning devices. Another tunable capacitor using a ferroelectric element in combination with a superconducting element is disclosed in U.S. Pat. No. 5,721,194. 
     Commonly owned U.S. patent application Ser. No. 09/419,126, filed Oct. 15, 1999, and titled “Voltage Tunable Varactors And Tunable Devices Including Such Varactors”, discloses voltage tunable dielectric varactors that operate at room temperature and various devices that include such varactors, and is hereby incorporated by reference. 
     There is a need for tunable filters that can operate at radio frequencies with reduced intermodulation products and at temperatures above those necessary for superconduction. 
     SUMMARY OF THE INVENTION 
     This invention provides an electronic filter including a substrate, a ground conductor, an input, an output, a first microstrip line positioned on the substrate and electrically coupled to the input and the output, and a first tunable dielectric varactor electrically connected between the microstrip line and the ground conductor. The input preferably includes a second microstrip line positioned on the substrate and having a portion lying parallel to the first microstrip line. The output preferable includes a third microstrip line positioned on the substrate and having a portion lying parallel to the first microstrip line. The first microstrip line includes a first end and a second end, the first end being open circuited and the varactor being connected between the second end and the ground conductor. The filter further includes a bias voltage circuit for supplying control voltage to the varactor. In the preferred embodiment, the bias circuit includes a high impedance line, a radial stub extending from the high impedance line, and a patch connected to the high impedance line for connection to a DC source. The varactor preferably includes a substrate having a low dielectric constant with a planar surface, a tunable dielectric layer on the planar substrate, with the tunable dielectric layer including a Barium Strontium Titanate composite, and first and second electrodes on the tunable dielectric layer and positioned to form a gap between the first and second electrodes. In a multiple pole embodiment, the filter further includes additional microstrip lines positioned on the filter substrate parallel to the first microstrip line and additional tunable dielectric varactors electrically connected between the additional microstrip lines and the ground conductor. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     FIG. 1 is a top plan view of a voltage tunable dielectric varactor that can be used in the filters of the present invention; 
     FIG. 2 is a cross sectional view of the varactor of FIG. 1, taken along line  2 — 2 ; 
     FIG. 3 is a graph that illustrates the properties of the dielectric varactor of FIG. 1; 
     FIG. 4 is a plan view of a tunable filter constructed in accordance with the preferred embodiment of this invention; 
     FIG. 5 is a cross sectional view of the filter of FIG. 4, taken along line  5 — 5 ; 
     FIG. 6 is a graph of a computer simulated frequency response of the tunable filter of FIG. 4 at zero bias with infinite Q of the varactors; 
     FIG. 7 is a graph of a computer simulated frequency response of the tunable filter of FIG. 4 at zero bias with 200 V bias with infinite Q of the varactors; 
     FIG. 8 is a graph of a computer simulated frequency response of the tunable filter of FIG. 4 at zero bias with 200 V bias with varactors having Q=50; and 
     FIG. 9 is a graph of a computer simulated frequency response of the tunable filter of FIG. 4 at zero bias with 200 V bias with varactors having Q=100. 
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     Referring to the drawings, FIGS. 1 and 2 are top and cross sectional views of a tunable dielectric varactor  10  that can be used in filters constructed in accordance with this invention. The varactor  10  includes a substrate  12  having a generally planar top surface  14 . A tunable ferroelectric layer  16  is positioned adjacent to the top surface of the substrate. A pair of metal electrodes  18  and  20  are positioned on top of the ferroelectric layer. The substrate  12  is comprised of a material having a relatively low permittivity such as MgO, Alumina, LaAlO 3 , Sapphire, or a ceramic. For the purposes of this description, a low permittivity is a permittivity of less than about 30. The tunable ferroelectric layer  16  is comprised of a material having a permittivity in a range from about 20 to about 2000, and having a tunability in the range from about 10% to about 80% when biased by an electric field of about 10 V/μm. The tunable dielectric layer is preferably comprised of Barium-Strontium Titanate, Ba x Sr 1−x TiO 3  (BSTO), where x can range from zero to one, or BSTO-composite ceramics. Examples of such BSTO composites include, but are not limited to: BSTO—MgO, BSTO—MgAl 2 O 4 , BSTO—CaTiO 3 , BSTO—MgTiO 3 , BSTO—MgSrZrTiO 6 , and combinations thereof. The tunable layer in one preferred embodiment of the varactor has a dielectric permittivity greater than 100 when subjected to typical DC bias voltages, for example, voltages ranging from about 5 volts to about 300 volts. A gap  22  of width g, is formed between the electrodes  18  and  20 . The gap width can be optimized to increase the ratio of the maximum capacitance C max  to the minimum capacitance C min  (C max /C min ) and increase the quality factor (Q) of the device. The optimal width, g, is the width at which the device has maximum C max /C min  and minimal loss tangent. The width of the gap can range from 5 to 50 μm depending on the performance requirements. 
     A controllable voltage source  24  is connected by lines  26  and  28  to electrodes  18  and  20 . This voltage source is used to supply a DC bias voltage to the ferroelectric layer, thereby controlling the permittivity of the layer. The varactor also includes an RF input  30  and an RF output  32 . The RF input and output are connected to electrodes  18  and  20 , respectively, such as by soldered or bonded connections. 
     In typical embodiments, the varactors may use gap widths of less than 50 μm, and the thickness of the ferroelectric layer ranges from about 0.1 μm to about 20 μm. A sealant  34  can be positioned within the gap and can be any non-conducting material with a high dielectric breakdown strength to allow the application of high voltage without arcing across the gap. Examples of the sealant include epoxy and polyurethane. 
     The length of the gap L can be adjusted by changing the length of the ends  36  and  38  of the electrodes. Variations in the length have a strong effect on the capacitance of the varactor. The gap length can be optimized for this parameter. Once the gap width has been selected, the capacitance becomes a linear function of the length L. For a desired capacitance, the length L can be determined experimentally, or through computer simulation. 
     The thickness of the tunable ferroelectric layer also has a strong effect on the C max /C min . The optimum thickness of the ferroelectric layer is the thickness at which the maximum C max /C min  occurs. The ferroelectric layer of the varactor of FIGS. 1 and 2 can be comprised of a thin film, thick film, or bulk ferroelectric material such as Barium-Strontium Titanate, Ba x Sr 1−x TiO 3  (BSTO), BSTO and various oxides, or a BSTO composite with various dopant materials added. All of these materials exhibit a low loss tangent. For the purposes of this description, for operation at frequencies ranging from about 1.0 GHz to about 10 GHz, the loss tangent would range from about 0.001 to about 0.005. For operation at frequencies ranging from about 10 GHz to about 20 GHz, the loss tangent would range from about 0.005 to about 0.01. For operation at frequencies ranging from about 20 GHz to about 30 GHz, the loss tangent would range from about 0.01 to about 0.02. 
     The electrodes may be fabricated in any geometry or shape containing a gap of predetermined width. The required current for manipulation of the capacitance of the varactors disclosed in this invention is typically less than 1 μA. In the preferred embodiment, the electrode material is gold. However, other conductors such as copper, silver or aluminum, may also be used. Gold is resistant to corrosion and can be readily bonded to the RF input and output. Copper provides high conductivity, and would typically be coated with gold for bonding or nickel for soldering. 
     Voltage tunable dielectric varactors as shown in FIGS. 1 and 2 can have Q factors ranging from about 50 to about 1000 when operated at frequencies ranging from about 1 GHz to about 40 GHz. The typical Q factor of the dielectric varactor is about 1000 to 200 at 1 GHz to 10 GHz, 200 to 100 at 10 GHz to 20 GHz, and 100 to 50 at 20 to 30 GHz. C max /C min  is about 2, which is generally independent of frequency. The capacitance (in pF) and the loss factor (tan δ) of a varactor measured at 20 GHz for gap distance of 10 μm at 300° K. is shown in FIG.  3 . Line  40  represents the capacitance and line  42  represents the loss tangent. 
     FIG. 4 is a plan view of a K-band microstrip comb-line tunable 3-pole filter  44 , tuned by dielectric varactors shown in FIGS. 1 and 2, constructed in accordance with the preferred embodiment of this invention. FIG. 5 is a cross sectional view of the filter of FIG. 4, taken along line  5 — 5 . Filter  44  includes a plurality of resonators in the form of microstrip lines  48 ,  50 , and  52  positioned on a planar surface of a substrate  56 . The microstrip lines extend in directions parallel to each other. Lines  46  and  54  serve as an input and an output respectively. Line  46  includes a first portion that extends parallel to line  48  for a distance L 1 . Line  54  includes a first portion that extends parallel to line  52  for a distance L 1 . Lines  46 ,  48  and  50  are equal in length and are positioned side by side with respect to each other. First ends  58 ,  60  and  62  of lines  46 ,  48  and  50  are unconnected, that is, open circuited. Second ends  64 ,  66  and  68  of lines  46 ,  48  and  50  are connected to a ground conductor  70  through tunable dielectric varactors  72 ,  74  and  76 . In the preferred embodiment, the varactors are constructed in accordance with FIGS. 1 and 2, and operate at room temperature. While a three-pole filter is described herein to illustrate the invention, microstrip combine filters of the present invention typically have 2 to 6 poles. Additional poles can be added by adding more strip line resonators in parallel to those shown in FIG.  4 . 
     A bias voltage circuit is connected to each of the varactors. However, for clarity, only one bias circuit  78  is shown in FIG.  4 . The bias circuit includes a variable voltage source  80  connected between ground  70  and a connection tab  82 . A high impedance line  84  connects tab  82  to line  52 . The high impedance line is a very narrow strip line. Because of its narrow width, its impedance is higher than the impedances of the other strip lines in the filter. A stub  86  extends from the high impedance line. The bias voltage circuit serves as a low pass filter to avoid RF signal leakage into the bias line. 
     The dielectric substrate  56  used in the preferred embodiment of the filter is RT5880 (ε=2.22) with a thickness of 0.508 mm (20 mils). Each of the three resonator lines  46 ,  48  and  50  includes one microstrip line serially connected to a varactor and ground. The other end of each microstrip line is an open-circuit. The open-end design simplifies the DC bias circuits for the varactors. In particular, no DC block is needed for the bias circuit. Each resonator line has a bias circuit. The bias circuit works as a low-pass filter, which includes a high impedance line, a radial stub, and a termination patch to connect to a voltage source. The first and last resonators  48  and  52  are coupled to input and output lines  46  and  54  of the filter, respectively, through the fringing fields coupling between them. Computer-optimized dimensions of microstrips of the tunable filter are L 1 =1.70 mm, L 2 =1.61 mm, S 1 =0.26 mm, S 2 =5.84 mm, W 1 =1.52 mm, and W 2 =2.00 mm. In the preferred embodiment, the substrate is RT5880 with a 0.508 mm thickness and the strip lines are 0.5 mm thick copper. A low loss (&lt;0.002) and low dielectric constant (&lt;3) substrate is desired for this application. Of course, low loss substrates can reduce filter insertion loss, while low dielectric constants can reduce dimension tolerance at this high frequency range. The lengths of the strip lines combined with the varactors determine the filter center frequency. The lengths L 1  or L 2  strongly affect the filter bandwidth. While the strip line resonators can be different lengths, in practice, the same length is typically used to make the design simple. The parallel orientation of the strip line resonators provides good coupling between them. However, input and output lines  46  and  54  can be bent in the sections that do not provide coupling to the strip line resonators. 
     The tunable filter in the preferred embodiment of the present invention has a microstrip comb-line structure. The resonators include microstrip lines, open-circuited at one end, with a dielectric varactor between the other end of each microstrip line and ground. Variation of the capacitance of the varactors is controlled by controlling the bias voltage applied to each varactor. This controls the resonant frequency of the resonators and tunes the center frequency of filter. The input and output microstrip lines are not resonators but coupling structures of the filter. Coupling between resonators is achieved through the fringing fields between resonator lines. The simple microstrip comb-line filter structure with high Q dielectric varactors makes the tunable filter have the advantages of low insertion loss, moderate tuning range, low intermodulation distortion, and low cost. The present filter can be integrated into RF systems, and therefore easily combined with other components existing in various radios. 
     FIG. 6 shows a computer-simulated frequency response of the tunable filter with non-biased varactors. The capacitance of each varactor is 0.2 pF at zero bias. The center frequency of the filter is 22 GHz. and the 3 dB bandwidth is 600 MHz. In FIGS. 6 through 9, curve S 21  represents the insertion loss, and curve S 11  represents the return loss. FIG. 7 is a simulated frequency response of the tunable filter at 200 V bias, where the capacitance of each varactor is 0.14 pF. The frequency of the filter is shifted to 23.2 GHz at 200 V bias. The bandwidth of the filter at 200 V is almost the same as the bandwidth at zero bias. 
     For data in FIGS. 6 and 7, it is assumed that the Q of varactors is infinite. FIG. 8 shows a frequency response of the filter at 200 V bias with varactors having a Q=50. The insertion loss about 3.8 dB. FIG. 9 shows a frequency response of the filter at 200 V bias with varactors having a Q=100. The insertion loss in this case is about 2.1 dB. 
     The preferred embodiment of this invention uses high Q and high power handling dielectric varactors as tuning elements for the filter. The dielectric varactor used in the preferred embodiment of the present invention is made from low loss (Ba,Sr)TIO 3 -based composite films. The typical Q factor of these dielectric varactors is 50 to 100 at 20 GHz with a capacitance ratio (C max /C min ) of around 2. A wide range of capacitance is available from the dielectric varactor, for example 0.1 pF to 1 nF. The tuning speed of the dielectric varactor is about 30 ns. Therefore, practical tuning speed is determined by the bias circuits. 
     The present invention provides a voltage-tuned filter having low insertion loss, fast tuning speed, and low cost that operates in the microwave frequency range, especially above 10 GHz. Since the dielectric varactors show high Q, low intermodulation distortion, and low cost, the tunable filters in the present invention have the advantage of low insertion loss, fast tuning, and high power handling. Simple structure and control circuits make the dielectric tunable filter low cost. 
     Accordingly, the present invention, by utilizing the unique application of high Q varactors, provides a high performance microwave tunable filter. While the present invention has been described in terms of what is believed to be its preferred embodiments, it will be apparent to those skilled in the art that various changes can be made to the disclosed embodiments without departing from the scope of this invention as defined by the following claims.