Abstract:
A method, an apparatus, and a computer program are provided to measure and/or correct duty cycles. Duty cycles of various signals, specifically clocking signals, are important. However, measurement of very high frequency signals, off-chip, and in a laboratory environment can be very difficult and present numerous problems. To combat problems associated with making off-chip measurements and adjustments of signal duty cycles, comparisons are made between input signals and divided input signals that allow for easy measurement and adjustment of on-chip signals, including clocking signals.

Description:
FIELD OF THE INVENTION 
   The present invention relates generally to duty cycle measurement and adjustment and, more particularly, to off-chip measurement and adjustment of high frequency signals. 
   DESCRIPTION OF THE RELATED ART 
   As the operating frequency of micro-processors has increased, the pulse width of the driving clocks is being reduced to such an extent that dynamic or static duty cycle corrections have become essential to ensure proper operation of logic circuits. In other environments, especially for slower operating frequencies, intentional duty cycle distortion is introduced to limit the ‘high state’ of a driving clock to prevent discharging of critical nodes. This, for example, is achieved by passing the driving clock through a pulse width limiter. In many present environments, this maximum pulse width is limited to a few hundred pico seconds. 
   For test purposes, it is very challenging to directly monitor multi-GHz signals and their associated duty cycle information. This is due to the bandwidth limitations of test equipments and their associated accessories, such as cables. A standard approach to test high frequency signals involves dividing them into lower frequency signals, which can then be easily characterized in a test setup. 
   However, frequency dividing of signals for monitoring, especially high frequency signals, can result in the loss of duty cycle information. Therefore, there is a need to monitor high frequency signals without substantial loss of duty cycle information in such a manner that addresses at least some of the concerns of conventional frequency monitoring. 
   SUMMARY OF THE INVENTION 
   The present invention provides a method, an apparatus, and a computer program product for measuring and correcting duty cycle information of a clock input signal source. A plurality of Low Pass Filters (LPFs) is employed. These LPFs output signals that are proportional to the duty cycles of input signals, where one signal is from the clock input signal source. A correction circuit is also employed that also receives a signal from the clock input signal source, and the correction circuit outputs a corrected clocking signal to one LPF of the plurality of LPFs. Based on the outputs of the LPFs, a comparator compares outputs of the LPFs to output a feedback signal to the correction circuit. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
     For a more complete understanding of the present invention and the advantages thereof, reference is now made to the following descriptions taken in conjunction with the accompanying drawings, in which: 
       FIG. 1  illustrates a circuit for monitoring high frequency circuits that allows for the regeneration of duty-cycle information; 
       FIG. 2  illustrates the output of the counter of  FIG. 1  corresponding to a percentage duty cycle for the circuit; and 
       FIG. 3  illustrates the outputs of LPF 1   130  and LPF 2   150  in  FIG. 1 . 
   

   DETAILED DESCRIPTION 
   In the following discussion, numerous specific details are set forth to provide a thorough understanding of the present invention. However, those skilled in the art will appreciate that the present invention may be practiced without such specific details. In other instances, well-known elements have been illustrated in schematic or block diagram form in order not to obscure the present invention in unnecessary detail. Additionally, for the most part, details concerning network communications, electro-magnetic signaling techniques, and the like, have been omitted inasmuch as such details are not considered necessary to obtain a complete understanding of the present invention, and are considered to be within the understanding of persons of ordinary skill in the relevant art. 
   It is further noted that, unless indicated otherwise, all functions described herein may be performed in either hardware or software, or some combinations thereof. In a preferred embodiment, however, the functions are performed by a processor such as a computer or an electronic data processor in accordance with code such as computer program code, software, and/or integrated circuits that are coded to perform such functions, unless indicated otherwise. 
   Generally, the circuit  100  can restore duty cycle information in a divided signal. This signal can, for example, be used during manufacturing testing to measure the duty cycle of an undivided signal. In one embodiment, the circuit is wholly digital or firmware, making it suitable for applications in advanced digital CMOS technology. Furthermore, unlike analog based implementations, this approach is robust against process-induced mismatches. In other words, there are many more process variation tolerances than a fully analog approach. Finally, with very little modification, this circuit can be used both to extract duty cycle information as well as to correct duty cycles. 
   The circuit  100  has a input high frequency CLK_IN. A first divider, divide-by-N (/N)  110  is coupled to the CLK_IN signal. A second divider, a divide-by-K  120  (/K) is coupled to the output of divider  110 . A reset for the n-bit counter  145  is coupled to the output of the divider  120  that can count from 1 to 2 n . A first low pass filter  130  (LPF 1 ) is coupled to the CLK_IN pulse. A digital duty cycle correction circuit (Digital DCC)  140  is coupled to the output of divider  110  and the counter  145 . The output of the DCC  140  is coupled to a LPF  2   150 . The output of the DCC  140  also becomes the CLK_OUT signal. The output of the LPF  1   130  and LPF  2   150  are coupled to the comparative inputs of a comparator  160 . The output of the comparator  160  is coupled to the UP/DOWN counter, as a function of the output of the comparator. 
   The n bit counter  145  is controlled both by the divide-by-K (/K) divider  120  and the output of the comparator  160 . The counter  145  increments/decrements its values on a specified edge of the output of the divide-by-K (/K) divider  120 . When there exists no trigger signal from the divider  120 , the counter  145  maintains its last value. Increment/decrement of the counter  145  is determined by the value output by the comparator  160 . 
   In one embodiment, when the comparator  160  output is high, the counter  145  increments, and when comparator  160  output is low, counter  145  decrements. The LPFs  130 ,  150  can be simple filters that can be realized using on chips resistors and capacitors. The comparator  160  can be a simple op amp or other input sensitive regenerative circuit. The divide-by-N (/N) and divide-by-K (/K) dividers  110 ,  120  can be basic digital dividers. The n output bits of the counter  145  select one of the 2 n  ‘delay elements’ in the digital DCC. Each delay element slows or makes faster, in the time domain, an edge of the input signal to the digital DCC  140 , thereby changing the duty cycle, but not the overall frequency. The output of the DCC  140  therefore will be a duty cycle corrected version of the input to the digital DCC  140 . 
   For purposes of illustration, a very high frequency signal CLK_IN is applied in the circuit  100 . That signal is input to LPF 1   130 . LPF 1   130  then outputs onto node B, which is one input of the comparator  160 , a low frequency (DC) signal that is representative of the duty cycle of CLK_IN. In one embodiment, LPF 1   130  has an output voltage such that when the duty cycle is 50%, node B is at VDD/2, where VDD is the power supply voltage. When the duty cycle is 100%, then node B is at VDD and when the duty cycle is at 0%, node B is at ground. Any duty cycle between 0% and 100% can be linearly interpolated between ground and VDD. 
   For ease of illustration, an example is that the duty cycle of the high frequency CLK_IN signal be equal to 70%. A divided version of CLK_IN as a function of the divider  110  is input into the digital DCC  140 . The input to the digital DCC  140  is labeled node A. Due to the division performed by divider  110 , there is no guarantee that the duty cycle at node A is the same as that of CLK_IN. This is because most dividers operate on the rising or falling edges of clocks, and, as a result, their output will not preserve the duty cycle information of their input. For instance, even though the duty cycle of CLK_IN can vary, the duty cycle of the divider  110  is typically fixed. 
   The counter  145  has n bits of output, so it can count from 1 to 2 n . For ease of illustration, the counter is initialized at 2 n−1 . In other words, this is the output at node F. Also the digital DCC  140  has 2 n  different delay elements. The delay element of the DCC  140  corresponding to count 2 n−1  is one that makes no duty cycle correction. For ease of illustration, delay elements above 2 n−1  will push out the falling edge of signal at node A in increasing increments, to result in increased duty cycle. For ease of illustration, delay elements below 2 n−1  will push in falling edge of the signal at node A in increasing increments to result in reduced duty cycle. In one embodiment, the frequency division (/N) is an even division and as a result the frequency signal at node A is output at 50% duty cycle. 
   The counter  145  is triggered by the signal at node E. The signal at node E is slow in frequency compared to that of node A. The comparator  160  can operate as follows. When the signal at node B is larger than that at node C, comparator  160  output at node D is high. When the signal at node B is smaller than that of node C, comparator  160  output at node D is low. The counter  150  is also controlled by node D. On a specified edge of node E, if node D is high, counter  145  increments on its previous value. On a specific edge of node E, if node D is low, counter  145  decrements on its previous value. 
   For example, node B is initially at a value corresponding to 70% duty cycle, while node C is at a value corresponding to 50% duty cycle. That is, CLK_OUT will initially have 50% duty cycle. Therefore, the comparator  160  output will be high. On the next rising edge of node E, the counter  160  increments its value to 2 n−1 +1. This will pass the signal at node A through a different delay element in the digital DCC  140 . This can increment the duty cycle of CLK_OUT to 50%+δ, where δ is the duty cycle increment introduced by the digital DCC  140 . CLK_OUT is then fed to LPF 2   150 , which will generate the corresponding low-frequency voltage on node C. The comparator  160  then compares nodes B and node C again, and this results in a new output at node D. If on the next rising edge of node E, the value of node D is still high, the counter  145  will increment its value to 2 n−1 +2, and the duty cycle of CLK_OUT will be 50%+2δ. This process will then continue until the duty cycle of CLK_OUT is as close as possible to the duty cycle of CLK_IN within the resolution of the digital DCC increments. 
   Generally, for any LPF to operate appropriately, it will need multiple cycles of an input signal to perform sufficient averaging operation. In the circuit  100 , the edges of node E rise and fall at a much slower rate than those at node A, due to the divider  120  divide-by-K (/K) value. As a result, the rate at which the counter  145  increments or decrements its output value at node F is much slower than that of the signal at node A. Consequently, having divider  120  allows LPF 2   150  to have sufficient time to perform the averaging. 
   In the circuit  100 , the digital DCC  140  has discreet increments of duty cycle. In one embodiment, the duty cycle of CLK_IN is not an exact match to any one of these duty cycle values. Such offsets can also be caused by mismatches in LPF 1   130  and LPF 2   150 , and also by offsets and dead zones associated with the comparator  160 . 
   For example, for a given count(X) of the counter  145 , CLK_OUT will have a 68% duty cycle, and at count X+1 of the counter  145 , CLK_OUT will have a 72% duty cycle. Let CLK_IN have a 70% DC. In this case, the counter  145  will be banging back and forth between count X and count X+1, and consequently CLK_OUT will be moving back and forth between duty cycle of 68% and 72%, every time there is a transition at node E. This could raise an alarm in terms of introducing jitter to CLK_OUT. However, consider the following case. 
   For ease of illustration, CLK_IN is a signal at 5 GHz and node A (and subsequently CLK_OUT), are to be used for test purposes and are much slower, perhaps 100 MHz. For ease of illustration, the digital DCC circuit  140  increments/decrements falling edges in very coarse increments of 100 pico-seconds. Such a large increment can also include any process induced mismatches. Therefore, the error in extracting the duty cycle information of CLK_IN by looking at CLK_OUT is as follows:
 
 DC=±( 100 ps/10000 ps)=±1/100=±1%  (1)
 
   Therefore, from this crude measurement, the duty cycle of CLK-IN can be calculated within ±1% accuracy. The accuracy of the above circuit  100  then depends on the frequency of CLK_OUT, and the discrete duty cycle steps available from the digital DCC circuit  140 . 
   In a further embodiment, the circuit  100  can be used to fix the duty cycle of CLK_OUT to any arbitrary duty cycle value. 
   Node B is therefore coupled to a voltage potential corresponding to a desired duty cycle value. Next CLK_IN is tied to node A, such that CLK_IN is undivided. Therefore, CLK_OUT will have the same frequency as CLK_IN. However, its duty cycle will be determined by the voltage at node B. 
   Turning now to  FIG. 2 , illustrated is a typical output from the counter  145 . For  FIG. 2 , the counter  145  was designed such that it will count from −8 to +8 with increments of 1. The digital DCC circuit  140  generates a duty cycle of 20% at −8, and 84% at 8, with increments of 4% duty cycle per unit counter increment/decrement. Divide-by-N (/N) of the divider  110  is set to divide-by-100 (/100) while divide-by-K (/K) of the divider  120  is set to divide-by-20 (/20). The duty cycle of CLK_IN is set 78%. For illustrative purposes, the duty cycle of CLK_IN is intentionally made so that it falls outside the duty cycle values provided by the digital DCC circuit. The nearest duty cycle values available from the digital DCC  140  are 76% and 80%. 
     FIG. 2  shows output from the counter  145 . Initially, the counter value is set at 0. This corresponds to 50% duty cycle. On every rising edge of node E of  FIG. 1 , the counter  145  value is incremented. Eventually the counter starts to bang back and forth between 6 and 7. 6 corresponds to duty cycle of 76%, and 7 corresponds to duty cycle of 80%. 
   Turning now to  FIG. 3 , illustrated are the outputs of LPF 1   130  and LPF 2   150  in  FIG. 1 . The output of LPF 1   130  corresponds to the duty cycle of CLK_IN. In the illustrated example, the steady state output of LPF 2   150  oscillates above and below that of LPF 1   130 . This is because the duty cycle of CLK_IN (78%) lies in between the available discrete duty cycle steps of 76% and 80%. 
   It is understood that the present invention can take many forms and embodiments. Accordingly, several variations may be made in the foregoing without departing from the spirit or the scope of the invention. The capabilities outlined herein allow for the possibility of a variety of programming models. This disclosure should not be read as preferring any particular programming model, but is instead directed to the underlying mechanisms on which these programming models can be built. 
   Having thus described the present invention by reference to certain of its preferred embodiments, it is noted that the embodiments disclosed are illustrative rather than limiting in nature and that a wide range of variations, modifications, changes, and substitutions are contemplated in the foregoing disclosure and, in some instances, some features of the present invention may be employed without a corresponding use of the other features. Many such variations and modifications may be considered desirable by those skilled in the art based upon a review of the foregoing description of preferred embodiments. Accordingly, it is appropriate that the appended claims be construed broadly and in a manner consistent with the scope of the invention.