Abstract:
A multistage circuit for regulating the charge voltage or the discharge current of a capacitance of an integrated device at a certain charge-pump generated boosted voltage is implemented without integrating high voltage transistor structures having a type of conductivity corresponding to the same sign of the boosted voltage (high-side transistors). The multistage circuit current includes at least a first stage, and an output stage in cascade to the first stage and coupled to the capacitance. The first stage is supplied at an unboosted power supply voltage of the integrated device, and the output stage is supplied at an unregulated charge-pump generated boosted voltage. The first stage includes a transistor having a type of conductivity corresponding to an opposite sign of the boosted voltage and of the power supply voltage. The drain of the output stage transistor is coupled to the boosted voltage either through a resistive pull-up or a voltage limiter.

Description:
FIELD OF THE INVENTION  
       [0001]     The present invention relates to integrated circuits that include charge-pump voltage boosting circuits, and in particular, to a multistage circuit for regulating a boosted voltage generated by a charge-pump voltage multiplier circuit or for regulating the discharging of a capacitance that may be charged at a boosted voltage.  
       BACKGROUND OF THE INVENTION  
       [0002]     Whenever certain circuits of an integrated device require supply, control or biasing voltages higher than the power supply voltage of the integrated device, it is a general practice of integrating dedicated charge-pump voltage multipliers for generating a boosted voltage of the required level.  
         [0003]     Often the boosted voltage generated by a common charge-pump circuit needs to be regulated for ensuring a correct bias. That is, a boosted voltage that remains within a specified range notwithstanding the current absorbed by the biased load or circuit. In these cases a dedicated circuit for regulating the voltage on an output node of the regulator to which the circuit or load to be powered, biased or controlled is connected. This configuration may generally be equated to a capacitive load. Similarly, a capacitance that eventually may be charged at a high voltage, e.g., at a charge-pump boosted voltage, may need to be discharged in a controlled manner such as with a certain discharge circuit. Also in this case, a dedicated regulating circuit needs to be integrated.  
         [0004]     An important example of an integrated device with these requirements is a non-volatile memory device that commonly requires biasing voltage levels higher than the power supply voltage of the device during program/erase phases of operation. For example, in a multi-level flash memory device of a NAND type, program/erase operations may require boosted voltages starting from around 10V and up to about 20-22V.  
         [0005]     In one-bit/cell flash memories, such a dedicated voltage regulator may be omitted and the output voltage of the charge-pump circuit be employed directly, without any regulation, by relying solely on the ON-OFF control of the charge-pump circuit that generates the boosted voltage. In one-bit/cell flash memories, a ripple of about 1V to 3V on the boosted voltage output by the ON-OFF controlled charge-pump circuit is generally tolerable.  
         [0006]     In contrast, in multi-level memory devices, where more bits can be stored in each single cell of the memory array, the much higher precision that is required for the biasing voltages makes indispensable integration of a dedicated boosted voltage regulator to reduce the amplitude of the ripple on the output biasing voltages that are required during different phases of operation of the memory.  
         [0007]     Similar requirements of precision for the output boosted voltages are encountered also in other integrated devices, in which cases the same requirement of integrating a dedicated regulating circuit of the boosted voltages generated by the charge-pump circuit arises.  
         [0008]     On a different account, fabrication technologies of integrated devices strive to contain costs. This cost awareness of chip manufacturing, especially for devices designed for mass production and intended primarily for consumer markets, imposes to produce devices at the lowest price per unit as possible. Technological advances in silicon processing are exploited to reduce the number of critical processing steps and the number of masks required.  
         [0009]     As noted above, an important example of this category of integrated devices are non-volatile memories. The fabrication technology of non-volatile memories is so streamlined for reducing costs that it does not generally permit formation along the normal low voltage (LV) CMOS structures special high voltage (HV) structures unless additional processing steps and relative masks are introduced for realizing the high side transistor of the CMOS structure. High voltage structures include transistors capable of withstanding a relatively high voltage. For a NAND type flash memory, which is generally supplied with positive voltages, both for the normal power supply voltage and for charge-pump boosted voltages, the high voltage transistor is the PMOS transistor. The low side transistor, generally the NMOS transistor, may be realized with an appropriate high voltage structure where needed without significant changes in terms of costs of the fabrication process.  
         [0010]     According to the most common fabrication processes of these types of integrated devices, the PMOS transistor of the CMOS pair (PMOS+NMOS) is the critical structure that does not admit voltage differences among its terminals (source, drain, gate and bulk) above about 4V to 5V, as readily known by those skilled in the art.  
         [0011]     When a positive boosted voltage regulating circuit to be supplied at an unregulated charge-pump boosted voltage in the range of 20-24V is required for fabricating a multilevel non-volatile flash memory, the normal low voltage PMOS transistor structure of the voltage regulator that is realized with the processing steps of any low cost one bit/cell flash memory fabrication process may often be intrinsically unsuitable. Therefore, additional costs of modifying the normal process introducing additional dedicated masks for realizing a high voltage PMOS structure cannot be avoided.  
         [0012]     To illustrate the problem,  FIG. 1  shows a typical multistage circuit powered at an unregulated charge-pump boosted voltage V PUMP  for regulating the voltage V OUT . In the example shown, the first stage is a differential stage, to a first input of which is coupled a reference (control) voltage V REF  and to a second input of which a scaled replica V FEED  of the output voltage V OUT  is fed back. The output stage is a PMOS transistor M POUT  that necessarily needs to have a high voltage structure in order to withstand the relatively high level of V PUMP , which is the unregulated charge-pump output voltage.  
         [0013]     In fact, as already mentioned, a similar problem of handling a charge-pump boosted voltage without integrating transistor structures of a conductivity type for the sign of the boosted voltage with special high voltage characteristics, arises when a capacitance that is eventually charged at a boosted voltage needs to be discharged with a current regulated by a dedicated regulating circuit.  
       SUMMARY OF THE INVENTION  
       [0014]     In view of the foregoing background, an object of the present invention is to provide a less expensive alternative approach to integrating high voltage PMOS structures specifically for implementing the required regulating circuits of a charge-pump generated boosted voltage, and of the discharge current of a capacitance charged at the boosted voltage.  
         [0015]     This cost saving objective is accomplished by a multistage circuit for regulating the charge voltage or the discharge current of a capacitance of an integrated device at a certain charge-pump generated boosted voltage that can be safely implemented without needing to integrate high voltage transistor structures of a type of conductivity for the same sign of the boosted voltage (i.e., the high-side transistors).  
         [0016]     Yet another object of the present invention is to provide a multi-level non-volatile flash memory device comprising a boosted voltage regulator that can be entirely fabricated with a low cost non-volatile flash memory fabrication process.  
         [0017]     Basically, the multistage circuit for regulating the charge voltage or the discharge current of a capacitance in an integrated device, comprising at least a first stage and an output stage in cascade to the first stage and coupled to the capacitance, has the first stage supplied at an unboosted power supply voltage of the integrated device. The output stage is supplied at an unregulated charge-pump generated boosted voltage and is composed of a transistor of a type of conductivity opposite for the sign of the boosted voltage and of the power supply voltage.  
         [0018]     The drain of the output stage transistor is coupled to the boosted voltage either through a resistive pull-up or a voltage limiter. 
     
    
     BIEF DESCRIPTION OF THE DRAWINGS  
       [0019]      FIG. 1  depicts a typical multistage voltage regulator of a charge-pump boosted voltage to be applied on a capacitance in accordance with the prior art.  
         [0020]      FIG. 2  depicts a multistage voltage regulator in accordance with the present invention that is functionally comparable to the voltage regulator of  FIG. 1 .  
         [0021]      FIG. 3  depicts an alternate embodiment of the voltage regulator of  FIG. 2  including an output follower stage functioning as an output current buffer.  
         [0022]      FIG. 4  depicts an alternate embodiment of a voltage regulator for charging the capacitance with a voltage ramp in accordance with the present invention.  
         [0023]      FIG. 5  is a graph illustrating the characteristics of the voltage regulator of  FIG. 4 .  
         [0024]      FIG. 6  depicts a multistage circuit for regulating the discharge current of a capacitance charged at a boosted voltage in accordance with the present invention.  
         [0025]      FIG. 7  depicts an alternate embodiment of the discharge current regulator circuit of  FIG. 4 . 
     
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS  
       [0026]     A first example embodiment of the invention, intended to provide a viable alternative to the known voltage regulator of  FIG. 1  without requiring the formation of any high voltage CMOS structure, is depicted in  FIG. 2 . As shown, the first stage M P1 , M P2 , M N1 , M N2 , M NT1  is a common differential stage  FIRST STAGE  (LV) that is powered at a normal (unboosted) power supply voltage V DD . The output stage  SECOND STAGE  (HV) is supplied at the unregulated charge-pump generated boosted voltage V PUMP .  
         [0027]     By powering the first stage  FIRST STAGE  (LV) at V DD , the PMOS transistors of the normal low voltage (LV) structure M P1  and M P2  may be used for the load current mirror of the two branches of the differential stage. The output stage  SECOND STAGE  (HV) is implemented by using a HV NMOS transistor M NOUT  with a resistive pull-up R PULL-UP  connected to the boosted voltage node V PUMP . The boosted voltage node V PUMP  is the output node of a charge-pump voltage multiplier (not shown) that generates the required boosted voltage V PUMP .  
         [0028]     In case of a relatively heavy capacitive load C LOAD  to be driven, the basic multistage voltage regulator circuit of  FIG. 2  may have an excessive consumption. In fact, assuming that the total capacitive load C LOAD  is about 100 pF, the time needed for charging the parasitic capacitance would be on the order of three to five times T rise , depending on the value of the output voltage to be produced on the capacitive load, wherein:
 
 T   rise   =C   LOAD   *R   PULL-UP   (1)
 
         [0029]     If a 100 pF capacitance needs to be completely charged at a certain programmed boosted voltage V OUT  in a 1 μs time interval, the value of the pull-up resistance should be:  
               R     pull   ⁢     -     ⁢   up       =       Trise     3   *   Cload       ≅     3   ⁢           ⁢   K   ⁢           ⁢   Ω               (   2   )             
 
         [0030]     Assuming that the voltage V OUT  to be produced on the load capacitance is 10V and that the unregulated boosted voltage output by the charge-pump circuit V PUMP  is 24V, the steady state current absorption from the charge-pump output node would be:  
               I     SUNK   ⁢           ⁢   22       =           (     24   -   10     )     ⁢           ⁢   V       2   ⁢           ⁢   K   ⁢           ⁢   Ω       ≅     5   ⁢           ⁢   mA               (   3   )             
 
         [0031]     Clearly, a charge-pump circuit of such a large current capability would be impractical in most cases, such as in a compact large capacity non-volatile memory device for example. To render current absorption independent from the load, an alternative embodiment of the basic circuit of  FIG. 2  may be as depicted in  FIG. 3 , according to which an output follower stage  FOLLOWER STAGE  (HV) that is a high slew rate stage is added as a current buffer to charge the load capacitance C LOAD  at the regulated boosted voltage V OUT .  
         [0032]     The follower stage is implemented with a high voltage NMOS transistor having its current terminals connected to the unregulated boosted voltage V PUMP  and to the output node V OUT , to which the resistive output voltage divider R 1 , R 2  of the feedback line V FEED  is connected.  
         [0033]     The advantage of this alternative embodiment is that at steady state, the current absorption of the output follower stage M NFOLL  will be an identical value to that of the prior art circuit of  FIG. 1 , which is given by:  
               I     SUNK   ⁢           ⁢   3   ⁢   F       =       I     SUNK   ⁢           ⁢   12       =       V   OUT         R   1     +     R   2                   (   4   )             
 
         [0034]     Differently from the first embodiment of  FIG. 2 , the capacitive load C LOAD  is no longer charged to V OUT  through the pull-up resistance R PULL-UP , but through the output follower stage M NFOL  that is capable of delivering relatively high currents at charge transients. The pull-up resistance R PULL-UP  is completely untied from the load and may be freely dimensioned for reducing steady state absorption from the charge-pump generator. In any case, such a pull-up resistance needs to be capable of charging the gate of the output follower transistor in a sufficiently short time.  
         [0035]     The difference from the circuit of  FIG. 2  is that according to this preferred embodiment, the load represented by the capacitance of the gate of the follower stage transistor is many orders of magnitude less than the driven capacitance C LOAD . Therefore, it is possible to employ a pull-up resistance on the order of hundreds of kilo-ohms.  
         [0036]     For example, using a pull-up resistance of 200 KΩ for a programmed V OUT  of 10V, and assuming that between the gate and source of the NMOS transistor M NFOLL  of the follower stage there is a voltage drop of a threshold (about 1V), the current absorbed from the charge-pump output will be given by:  
             I   =           (     24   -   11     )     ⁢           ⁢   V       200   ⁢           ⁢   K   ⁢           ⁢   Ω       ≅     65   ⁢           ⁢   µ   ⁢           ⁢   A               (   5   )             
 
         [0037]     Such a current consumption of the regulating circuit is practically about the same as that of the first differential stage of the prior art regulator of  FIG. 1 . Of course, for higher output voltages the current consumption of the regulating circuit will decrease.  
         [0038]     To summarize, when comparing the current absorption of the regulator of  FIG. 3  with that of the prior art circuit of  FIG. 1 , the following remarks may be made. The output follower stage consumes as the output stage of the prior art circuit of  FIG. 1  (I SUNK3F =I SUNK22 ). The first stage of the regulator circuit of the invention, being supplied at V DD , does not absorb current from the charge-pump. The second stage of the circuit of  FIG. 3  practically absorbs about the same current as the first differential stage of the prior art circuit of  FIG. 1  (I SUNK32 =I SUNK11 ). Therefore, according to the embodiment of  FIG. 3 , the multistage regulating circuit does not have a current absorption from the charge-pump greater than the prior art circuit of  FIG. 1 .  
         [0039]     By simulating operation, the circuit according to the embodiment of  FIG. 3  has performances in terms of gain, cut off frequency, transients and PSRR, equal or better than the prior art circuit of  FIG. 1 . Of course, at it will be evident to those skilled in the art, the circuit of  FIG. 3  may be improved further in terms of maximum output voltage handling capability by employing transistors formed in a triple well (for eliminating the body effect on the follower stage) and natural transistors (for reducing the gate-source voltage drop of the follower stage.  
         [0040]     A further embodiment of a voltage regulator for charging the load capacitance C LOAD  with a voltage ramp by applying to the input V REF  a low voltage control ramp is depicted in  FIG. 4 . The control low voltage ramp applied to the V REF  input node of the first differential stage is amplified and reproduced on the node OUTSSTG.  
         [0041]     On the output node V OUT  a voltage ramp equal to OUTFSG less the threshold of the M NDRIVER  will be generated. The relative voltage characteristics are shown in  FIG. 5 . An open loop regulation is implemented for driving heavy capacitive loads without encountering stability problems in the feedback part of the multistage voltage regulator circuit.  
         [0042]      FIG. 6  shows a different embodiment useful for regulating the discharge current of a capacitance C LOAD  that during operation of the integrated device is charged at a boosted voltage. For example, for discharging the well region of a flash memory cell array at the end of an ERASE operation when the well may be charged at 22V.  
         [0043]     The low voltage part of the regulating circuit, that is the first stage  FIRST STAGE  (LV) that is supplied at a normal (LV) power supply voltage V DD , is composed of a low voltage current generator (LV), a first current mirror referred to V DD , and made with LV PMOS transistors M P0  and M P1 , and a second current mirror referred to a ground potential made with LV NMOS transistors M N1  and M N2 . The drain of the low voltage NMOS transistor M N2  is connected to the load capacitance C LOAD  to be discharged through a drain limiter stage, composed of the inverter I V1  and by the high voltage output NMOS transistor M N3  that forms a high voltage output stage  SECOND STAGE  ( HV ) coupled to the capacitance C LOAD  charged at the boosted voltage of the node OUT.  
         [0044]     In this way, the node OUT (e.g., the well of the memory array) that is charged at a relatively high boosted voltage (e.g., 22V) is effectively decoupled from the drain node of the low voltage transistor M N2  of the second current mirror of the first stage by the high voltage output stage  SECOND STAGE  ( HV ) , which is formed by the high voltage NMOS output transistor M N3 .  
         [0045]     In this way, a regulating circuit for discharging at a certain constant current a capacitance C LOAD  that is charged at a boosted voltage is provided, the control part of which  FIRST STAGE  ( LV ) is entirely made with low voltage transistors. This enhances reliability and performance while decreasing area occupation and consumption.  
         [0046]     An alternative embodiment of such a regulating circuit for discharging at a controlled current a capacitance charged at a boosted voltage is shown in  FIG. 7 . According to this alternative embodiment, instead of employing a drain limiter circuit, the pair of NMOS transistors forming the second current mirror M N1  and M N2  are both formed with a high voltage structure. In this case, the second current mirror forms the output high voltage stage  SECOND STAGE  (HV) of the two stage regulating circuit.