Abstract:
The invention relates to a high-frequency transmission line including a conductive tape ( 6 ) associated with a shielding surface ( 4 ) that is placed under the line structure and is divided into parallel microstrips in a direction generally orthogonal to the direction of the line, said microstrips being movable relative to the conductive tape.

Description:
FIELD OF THE INVENTION 
     The present invention relates to a radio frequency (RF) transmission line. Radio frequency waves belong to the millimetric or submillimetric range, for example, to a frequency range from 10 to 500 GHz. 
     DISCUSSION OF PRIOR ART 
     The continual development of integrated circuits on silicon allows operations at very high frequencies in the radio frequency range. The passive elements used comprise adapters, attenuators, power dividers, and filters. Transmission lines connecting these elements form a basic element in an RF circuit. To make use of the silicon technology, transmission lines on chips with a high quality factor are required. Indeed, the quality factor is an essential parameter since it stands for the insertion loss of a transmission line for a given phase shift. Further, such lines must provide a determined phase shift and have a determined characteristic impedance for the frequency used. 
     Generally, the transmission lines are formed of a conductive tape having lateral dimensions ranging from 10 to 50 μm and a thickness on the order of one μm (from 0.5 to 3 μm according to the technology used). The conductive tape is surrounded with one or several lateral, upper or lower conductors forming ground planes intended to form a waveguide-type structure with the conductive tape. In technologies compatible with the forming of electronic integrated circuits, the conductive tape and the ground planes are formed of elements of metallization levels formed above a semiconductor substrate. 
     A type of transmission line with a particularly high performance is disclosed in U.S. Pat. No. 6,950,590, having its FIG. 4a copied in  FIG. 1  hereof. On a silicon substrate  128  coated with metal levels separated by an insulator  127 , is formed a lower ground plane  136  divided into parallel strips of small width, for example, ranging between 0.1 and 3 μm. In a higher metallization level is formed a central conductive tape  122  forming the actual transmission line, surrounded with lateral coplanar ground tapes  124 ,  126 . 
     Features and advantages of such a line are described in detail in the above-mentioned patent. Central tape  122  and ground lines  124  and  126  being coplanar, this structure is currently called a coplanar waveguide, or CPW. Further, as indicated in this patent, the structure forms a slow wave coplanar waveguide, or S-CPW. 
     In a structure such as that in  FIG. 1 , the dimensions of the various elements are optimized to obtain, at a determined frequency, given phase characteristics as well as a given characteristic impedance. It is not possible to modify these characteristics once the line has been formed. For example, it is not possible to form a phase shifter having a given identical phase shift for several different frequencies, or an impedance matcher enabling to match various impedances. 
     SUMMARY 
     Thus, the present invention provides a transmission line of coplanar waveguide type which is particularly capable of being integrated on microelectronic integrated circuits wherein various parameters of the waveguide are adjustable to optimize the phase shift at a selected frequency and for a selected characteristic impedance, and to modify the line parameters to match with a different operating frequency or with a different characteristic impedance. 
     It is thus desired to form a transmission line where the characteristic impedance and the delay (that is, the phase difference between the signal at the line input and the signal at the line output) can be optimized independently. 
     An embodiment of the present invention provides a high-frequency transmission line comprising a conductive tape associated with at least one conductive plane, wherein at least one conductive plane is mobile with respect to the conductive tape. 
     According to an embodiment of the present invention, the transmission line is of slow wave coplanar waveguide type. 
     According to an embodiment of the present invention, at least one conductive plane is a shielding plane arranged under the line structure and divided into parallel microstrips having a general direction orthogonal to the line direction. 
     According to an embodiment of the present invention, the transmission line comprises electrostatic means for displacing the conductive plane. 
     According to an embodiment of the present invention, the transmission line comprises a second conductive plane under the shielding plane. 
     According to an embodiment of the present invention, the transmission line comprises means for selectively biasing the various microstrips. 
     According to an embodiment of the present invention, at least one conductive plane is formed of mobile coplanar ground tapes laterally surrounding the conductive tape. 
     According to an embodiment of the present invention, the transmission line comprises means for electrostatically shifting the ground tapes in a lateral direction. 
     According to an embodiment of the present invention, the transmission line comprises, on a semiconductor substrate, a first conductive plane, a second conductive plane or shielding plane divided into microstrips, a conductive tape surrounded with ground tapes, a cavity extending under a portion at least of the length of the tapes and of the shielding plane all the way to the vicinity of the first conductive plane. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       The foregoing and other objects, features and advantages of the present invention will be discussed in detail in the following non-limiting description of specific embodiments in connection with the accompanying drawings, among which: 
         FIG. 1  is a copy of FIG. 4a of U.S. Pat. No. 6,950,590; 
         FIGS. 2A ,  2 B, and  2 C are cross-section views of a transmission line according to an embodiment of the present invention, in three positions; 
         FIGS. 3A ,  3 B, and  3 C respectively are a cross-section view, a perspective view, and a top view of a transmission line according to an embodiment of the present invention; and 
         FIG. 4  is a top view of another embodiment of the tunable slow wave coplanar waveguide (TS-CPW) of the present invention. 
     
    
    
     It should be noted that generally, as usual in the representation of microelectronic components, the elements of the various drawings are not to scale. 
     DETAILED DESCRIPTION 
       FIGS. 2A-2C  are cross-section views of an S-CPW type transmission line. A perspective view of this structure would be similar to that illustrated in  FIG. 1 . 
     Referring to  FIGS. 2A ,  2 B, and  2 C, on a substrate  1  (also shown in  FIGS. 3A ,  3 B and  4 ), for example, a semiconductor substrate, for example, made of silicon, are formed metallization levels separated by an insulating material  2  (also shown in  FIGS. 3A ,  3 B, and  4 ). In an intermediary metallization level is formed a shielding plane divided in microstrips  4  similar to structure  136  of  FIG. 1 . Above this metallization level is formed a central transmission tape  6  similar to tape  122  of  FIG. 1  and, on either side of this central tape are formed lateral ground tapes  8  and  9  similar to ground tapes  124  and  126  of  FIG. 1 . 
     Further, in the shown embodiment of  FIGS. 2A ,  2 B, and  2 C, a metallization plane  10  is provided at a lower level. Plane  10  may be divided into microstrips parallel to those of shielding plane  4 . 
     As shown in  FIGS. 2A   2 B, and  2 C, a cavity  12  is provided which defines a vacuum space under central tape  6  and on either side thereof. In the shown example, cavity  12  extends in the insulating material across the width of the central tape and of the lateral tapes, stopping a little above metallization level  10 . Thus, the microstrips of shielding plane  4  are laterally anchored in insulating material  2  and their central portion is free. If a D.C. potential difference is applied between metallization planes  4  and  10 , the metal microstrips of shielding plane  4  will be attracted downwards by metallization  10 , as shown in  FIG. 2B . Conversely, if a potential difference is applied between line  6  and the microstrips of shielding plane  4 , the microstrips will be attracted upwards by line  6 , as shown in  FIG. 2C . It should be noted that an insulator, not shown, is formed under tape  6  and/or on the microstrips to avoid shorting these elements. 
     Although this is not shown in the cross-section view of  FIG. 2A , it should be clear that a portion only of the line length is located above cavity  12  and that each of the tapes of the line (the central tape and the lateral ground tapes) bears against insulating portions located at the back and at the front of the cross-section plane. 
     Decreasing or increasing the distance between strip  6  and the elements of shielding plane  4  will have as a main effect to modify equivalent capacitance C eq  of the transmission line. This causes a modification of characteristic impedance Z=(L eq /C eq ) 1/2  of the line, L eq  being the equivalent inductance of the line. Correlatively, the phase velocity of the propagation signal, v φ =1/(L eq ·C eq ) 1/2 , will be modified, which results in a modification of the electric length of the line, θ=l(ω/v φ ), where l stands for the physical length of the transmission line and ω for the angular frequency of the signal. 
     C eq  could be modified by applying variable potential differences between ground plane  4  and lower metallization plane  10  or the transmission line. However, it will be preferred, in practice, to act in all or nothing by applying potentials such that, in the idle state, the microstrips of shielding plane  4  are substantially horizontal ( FIG. 2A ), in a second state, these strips are in a low end position ( FIG. 2B ) and, in a third state, the strips are in a high end state ( FIG. 2C ). 
     To finely adjust the capacitance variation, it may be provided to selectively move a selected number of strips of shielding plane  4  by applying the potential capable of generating an electrostatic attraction force with the lower conductive plane or with the conductive tape by selectively biasing a selected number of these conductive tapes. 
     As seen previously, the ability to selectively modify equivalent capacitance C eq  results in an ability to modify the characteristic line impedance and the phase velocity of a signal in the line. This however does not enable to independently set the two parameters. To enable to independently set the characteristic impedance and the phase velocity, an embodiment of the present invention provides for the lateral distance between the lateral ground tapes and the central tape to be settable, which essentially results in modifying equivalent inductance L eq  of the line. 
     A first embodiment of a structure enabling to obtain this independent setting is illustrated in  FIGS. 3A ,  3 B,  3 C which respectively are a cross-section view, a perspective view, and a top view.  FIGS. 3A ,  3 B, and  3 C will be collectively described hereinafter. 
     The structure of  FIGS. 3A ,  3 B, and  3 C is similar to that of  FIG. 2A . It comprises lower conductive plane  10  ( FIG. 3A ), intermediary plane  4 , and central tape line  6  surrounded with ground tapes  8  and  9 . While in the case of the structure of  FIGS. 2A ,  2 B and  2 C, ground tapes  8  and  9  were not necessarily totally comprised above cavity  12  ( FIGS. 3A and 3C ), they are now, to be able to be laterally mobile under the effect of a voltage difference between these ground tapes and external lateral electrodes  21 ,  22 . Ground tapes  8  and  9  are connected to pads  23 - 1 ,  23 - 2 , and  24 - 1 ,  24 - 2  respectively formed on insulator  2  by blades  25 - 1 ,  25 - 2 , and  26 - 1 ,  26 - 2 , as shown in  FIG. 3C . Blades  25 - 1 ,  25 - 2 , and  26 - 1 ,  26 - 2  form a spring and enable a displacement of ground tapes  8  and  9  when they are attracted by external electrodes  21 ,  22 . Of course, an electrostatic attraction between the central conductor and ground planes  8  and  9  may also be provided. 
     Stop systems may be provided to limit the displacement of ground planes and avoid a short-circuit between these ground planes and electrodes  21 ,  22  or central conductor  6 . Such stops may for example be formed on insulating layers deposited on the lateral surfaces of the various elements. 
     This relative displacement of the lateral ground tapes with respect to the central tape mainly results in modifying equivalent inductance L eq  of the transmission line. L eq  and C eq , and thus Z and v φ , can thus be set independently. 
       FIG. 4  is a top view illustrating an alternative embodiment of the present invention. The transmission line is divided into a succession  30 - 1 ,  30 - 2  . . .  30 - n  of n line elements, each of which has the structure illustrated in  FIGS. 3A ,  3 B,  3 C. It should be understood that this multiplies setting possibilities. 
     The present invention is likely to have various alterations, modifications, and improvements which will readily occur to those skilled in the art. Various means may be used to displace the shielding plane, the central tape, and the lateral ground tapes with respect to one another. 
     The present invention has been described in the context of a specific example of its application to an S-CPW type structure. It should however be understood that it generally applies to other types of tape transmission lines having parameters depending on the distance(s) between this tape and various ground planes. 
     As indicated previously, for the displacement of shielding plane  4 , it may be provided for this displacement to be only possible upwards, or only downwards. It may also be provided for this displacement to be selective, that is, for the different microstrips of the structure forming shielding plane  4  to be able to be displaced individually. In the detailed embodiment, the microstrips are embedded at their two ends. It may also be provided for these microstrips to be interrupted in their middle portion and to be embedded at a single one of their ends (under central tape  6  or under ground tapes  8 ,  9 ) to form embedded beams. In this case, it may be provided that at least a central portion of the central tape or of the ground tapes is laid on an insulator to embed the beams which form shielding plane  4 . 
     Various alternative embodiments may also be used as concerns lateral displacements. In particular, attraction electrodes  21  and  22  and ground tapes  8 ,  9  may be coupled by interdigited structures, as shown in  FIGS. 3B and 3C . Further, the blades forming springs  25 - 1 ,  25 - 2 ,  26 - 1 ,  26 - 2  ( FIG. 3C ) may have various configurations, for example, meander shapes. 
     One of the advantages of the structure described herein is that it is compatible with current techniques for forming metallization levels generally used to form interconnects above a microelectronic integrated circuit. 
     As an example only, the following dimensions may be selected for a transmission line intended to operate at frequencies close to 60 GHz:
         tape width and distance between tapes  6 ,  8 ,  9 : ranging between 7 and 15 μm;   vertical distance between metallization levels: ranging between 0.5 and 2 μm;   distance between ground tapes  8  and  9  and electrodes  21  and  22 : ranging between 0.5 and 2 μm.       

     Such values enable to control the electrostatic displacement of the various elements with voltages having values on the order of some ten volts and to cause variations of the capacitance and inductance values by a factor ranging between 1.5 and 3.