Abstract:
A touch switch apparatus for detecting the presence of an object such as a human appendage, the apparatus having a touch pad and a local control circuit connected to the touch pad and to a controlled device. The touch pad preferable includes a first electrode and a second electrode spaced from and surrounding the first electrode. The control circuit is preferably in integrated circuit form. A signal is provided to the touch pad to generate an electric field thereabout. Introduction of a stimulus near the touch pad disturbs the electric field. The control circuit detects the electric field disturbance in and generates a control signal in response.

Description:
CROSS REFERENCE TO RELATED APPLICATIONS 
   This application is a continuation of, and claims priority from, application Ser. No. 10/027,884 filed on Oct. 25, 2001 now U.S. Pat. No. 6,713,897 which is a continuation of application Ser. No. 09/234,150 filed on Jan. 19, 1999 (now U.S. Pat. No. 6,320,282). 

   FIELD OF THE INVENTION 
   The present invention relates to touch panel systems and, more particularly, to touch switches (i.e., switches that are operated, for example, by touching a finger to or about a touch pad) and related control circuits for use as replacements for mechanical switches. 
   BACKGROUND OF THE INVENTION 
   Mechanical switches have long been used to control apparatus of all types, including household appliances, machine tools, and other domestic and industrial equipment. Mechanical switches are typically mounted on a substrate and require some type of penetration through the substrate. These penetrations, as well as penetrations in the switch itself, can allow dirt, water and other contaminants to pass through the substrate or become trapped within the switch, thus leading to electrical shorts and other malfunctions. 
   Touch switches are often used to replace conventional mechanical switches. Unlike mechanical switches, touch switches contain no moving parts to break or wear out. Moreover, touch switches can be mounted or formed on a continuous substrate sheet, i.e. a switch panel, without the need for openings in the substrate. The use of touch switches in place of mechanical switches can therefore be advantageous, particularly in environments where contaminants are likely to be present. Touch switch panels are also easier to clean than typical mechanical switch panels because they can be made without openings in the substrate that would allow penetration of contaminants. 
   Known touch switches typically comprise a touch pad having one or more electrodes. The touch pads communicate with control or interface circuits which are often complicated and remote from the touch pads. A signal is usually provided to one or more of the electrodes comprising the touch pad, creating an electric field about the affected electrodes. The control/interface circuits detect disturbances to the electric fields and cause a response to be generated for use by a controlled device. 
   Although touch switches solve many problems associated with mechanical switches, known touch switch designs are not perfect. For example, many known touch switches can malfunction when contaminants such as water or other liquids are present on the substrate. The contaminant can act as a conductor for the electric fields created about the touch pads, causing unintended switch actuations. This presents a problem in areas where such contaminants are commonly found, such as a kitchen and some factory environments. 
   Existing touch switch designs can also suffer from problems associated with crosstalk, i.e., interference between the electric fields about adjacent touch pads. Crosstalk can cause the wrong touch switch to be actuated or can cause two switches to be actuated simultaneously by a touch proximate a single touch pad. 
   Many known touch switch designs are also susceptible to unintended actuations due to electrical noise or other interferences affecting a touch pad itself, or the leads extending from the touch pad to its associated control circuit. This problem can be aggravated in applications where the touch pad is a relatively large distance away from the control circuitry, as is frequently the case with conventional touch switch designs. 
   Existing touch switch designs commonly require complicated control circuits in order to interface with the devices they control. These control circuits are likely to be comprised of a large number of discrete components which occupy considerable space on a circuit board. Because of their physical size, the control circuits are typically located at a substantial distance from the touch pads themselves. The physical size of the control/interface circuits and their remoteness from the touch pads can aggravate many of the problems discussed above, such as crosstalk and susceptibility to electrical noise and interference. The size and remoteness also complicate the overall touch switch panel design, resulting in increased production cost and complexity. 
   Some known touch switch designs require a separate grounding lead from the touch pad to the interface/control circuit or to the controlled device. Certain apparatus utilizing conventional mechanical switches do not require, and may not readily accommodate, such grounding leads. Adapting such apparatus for use with such touch switches can require the addition of special grounding provisions, thus increasing design and production time, complexity, and cost. These ground lead requirements can preclude simple, direct replacement of conventional mechanical switch panels with touch switch panels. 
   Recent improvements in touch switch design include techniques which lower the input and output impedance of the touch switch itself, thereby making it highly immune to false actuations due to contaminants and external noise sources. U.S. Pat. No. 5,594,222 describes a low impedance touch switch design which is less susceptible to malfunction in the presence of contaminants and electrical noise than many previous designs. Even though this approach has several advantages over the prior art, there are some attributes that may limit its application. For instance, the resulting switch may be sensitive to temperature variations. As long as the temperature variations at the output are small relative to legitimate signal changes and are small relative to signal variations induced by transistor variations, then a single transistor or other amplifying device will be quite satisfactory. However, this technique may require the use of additional circuitry to interface with the controlled device, thus increasing cost and complexity to the overall touch switch design. In applications where there is little dynamic range to allow for compensation, and where temperature changes are significant relative to legitimate signal changes, a different approach may be better able to eliminate or reduce the effects of temperature. 
   Also, even though the low impedance approach of this technique can differentiate between contaminants with some finite amount of impedance and a human touch with some finite amount of impedance, this technique may not be enough to differentiate between extremely low levels of impedance. Such a situation could exist when an entire touch switch (i.e., both the inner and outer electrode) is covered with a large amount of contaminant. A similar, essentially zero-impedance, situation could exist when a conductive material, such as a metal pan, entirely covers a touch switch. 
   U.S. patent application Ser. No. 08/986,927, assigned to the same assignee as the present application, and hereby incorporated by reference herein, discloses a touch switch apparatus having a differential measuring circuit which addresses many of the problems related to common mode disturbances affecting touch switches. For example, a touch switch having a two-electrode touch pad can be configured to generate an electric field about each electrode. A common mode disturbance, such as a contaminant substantially covering both electrodes, is likely to affect the electric field about each of the electrodes substantially equally. Each electrode provides a signal proportional to the disturbance to the differential measuring circuit. Since the signals from the electrodes are therefore contemplated to be substantially equal, the differential measuring circuit does not sense a differential and does not respond to the common mode disturbance. On the other hand, if the field about only one of the electrodes is disturbed, the signal provided by that electrode to the differential measuring circuit will likely be substantially different than that provided by the other, non-affected electrode. The differential circuit can respond by providing an output which causes a switch actuation. 
   Although the differential measuring circuit approach addresses many problems known in the prior art, it is relatively complex and can be costly to design and manufacture. A differential measuring circuit typically comprises many more parts than a more conventional control circuit. The additional parts are likely to take up more space on a touch switch panel. As such, the control circuit is likely to be even farther from the touch pad than it might be with a non-differential circuit design, requiring long leads between the touch pad and its control circuit. This can actually aggravate concerns related to electrical interference. Furthermore, when building a differential measuring circuit, matching of components becomes important. Proper component matching presents an additional manufacturing burden and is likely to add cost. 
   Although the foregoing improvements can reduce unintended switch actuations as a result of crosstalk between switches and the effects of electrical interference on their control circuits, they do not eliminate these problems completely. Furthermore, they do not address the need for separate grounding circuits in certain touch switch applications or resolve the concerns related thereto. 
   SUMMARY OF INVENTION 
   It is an object of the invention to provide a reliable touch switch apparatus which is substantially unaffected by the presence of contaminants, electrical interference, and other disturbances proximate the touch switch and its associated control circuitry so as to prevent unintended switch actuation when the touch switch is affected by such disturbances. 
   It is also an object of the invention to simplify the interface requirements between touch switches and the many different applications in which they can be used, so that touch switch panels can readily serve as direct, plug-in replacements for mechanical switch panels. 
   The present invention provides a touch switch apparatus comprising a touch pad and a control circuit located near the touch pad. The touch pad and control circuit may be mounted on a dielectric substrate. The control circuit is small compared to the overall size of the apparatus. In a preferred embodiment, the control circuit is substantially reduced to one or more integrated circuits. The physical compactness of the control circuit in the integrated circuit embodiment reduces the touch switch&#39;s susceptibility to common mode interference and to crosstalk and interference between adjacent touch switches. The integrated circuit approach also provides for better matching and balancing of the control circuit components. 
   The touch switch of the present invention can be configured in a variety of preferred embodiments. In some embodiments, the touch switch can emulate a conventional, maintained-contact type of mechanical switch. In other embodiments, the touch switch can emulate a momentary-contact type of mechanical switch. 
   In a preferred embodiment, the touch pad has a first electrode and a second electrode proximate the first electrode. At least one of the electrodes is electrically coupled to the local control circuit. The first and second electrodes and the local control circuit are typically placed on the same surface of a substrate, opposite the side of the substrate to be used as the touch surface. However, they need not be coplanar, and may be placed on opposite sides of a substrate. 
   In an alternate embodiment, the touch pad has a single electrode which is electrically coupled to the local control circuit. In other alternate embodiments, the touch pad can have more than two electrodes. 
   In a preferred embodiment, the control circuit includes means for generating a signal and providing it to the touch pad to create an electric field about one or more of the electrodes comprising the touch pad. Alternatively, such a signal may be generated elsewhere and provided to one or more of the electrodes to create one or more electric fields thereabout. The control circuit detects disturbances to the electric fields in response to stimuli thereto, such as a user&#39;s fingertip contacting or approaching the substrate adjacent the touch switch. The control circuit selectively responds to such field disturbances by generating a control signal for use by a controlled device, such as a household appliance or an industrial machine. 
   In a preferred embodiment, the control circuit detects and responds to differences in electrical potential between the first and second electrodes in response to the introduction of a stimulus in proximity to either the first electrode, the second electrode, or both. Such differential measuring circuit provides for the rejection of common mode signals (i.e., signals that would tend to affect both electrodes approximately equally) such as temperature, electrical noise, power supply variations, and other inputs. The differential measuring circuit also provides for the rejection of common mode signals resulting from the application of contaminants to the substrate adjacent the touch switch. 
   In a preferred embodiment, a signal is applied to a first electrode and to a second electrode. An electric potential is developed at each electrode, and, consequently, an electric field is generated each of the electrodes. Two matched transistors are arranged in a differential measuring circuit, with the first transistor connected to the first electrode and the second transistor connected to the second electrode. Each transistor&#39;s output is connected to a peak detector circuit, and the output of each peak detector circuit is in turn provided to a decision circuit. 
   Each transistor&#39;s output is altered when the electric field about its corresponding electrode is altered, such as when the electrode is touched or approached by a user. The peak detector circuits respond to changes in the transistors&#39; outputs and provide signals corresponding to the peak potentials from the transistors to the decision circuit. The decision circuit uses the peak potentials in a predetermined manner to provide an output for use by other portions of the control circuit. 
   In a preferred embodiment, the inner and outer electrodes are operably associated with the inputs to the decision circuit such that when a disturbance to an electric field about a first electrode is greater than the degree of disturbance of an electric field about a second electrode, the decision circuit will provide a high level output. Conversely, the decision circuit will provide a low level output when a disturbance to the electric field about the second electrode is greater than the degree of disturbance of an electric field about the first electrode. When the fields about both electrodes are disturbed more or less equally, the decision circuit will provide a low level output. 
   The first condition can be created, for example, when a fingertip substantially covers the first electrode but not the second electrode. The second condition can be created, for example, when a fingertip or contaminant substantially covers the second electrode but not the first electrode. The third condition can be created, for example, when a contaminant or an object, such as a metal pan, covers both the first and second electrodes. 
   The decision circuit output is provided to other circuit components, such as an electrical latch, which selectively cause a control signal to be output from the control circuit, depending on the decision circuit output state. In a preferred embodiment, a high level output from the decision circuit ultimately causes a control signal to be output from the control circuit, while no control signal will be output in response to a low level output. In an alternate embodiment, a low level output from the decision circuit causes a control signal to be output from the control circuit, while no control signal will be output in response to a high level output. 
   The touch switch apparatus of the present invention can be used to perform almost any function which can be performed by a mechanical switch, such as turning a device on or off, adjusting temperature, or setting a clock or timer. It can be used in place of, and solve problems associated with, existing touch switches. It can also be used as a direct replacement for mechanical membrane-type switches. The touch switch apparatus of the present invention is well suited for use in environments where temperature variations are extreme, where substantial amounts of contaminants can be present or where metal objects may be placed on or over the touch pad. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
     The various features, advantages and other uses of the present invention will become more apparent by referring to the following detailed description and drawings in which: 
       FIG. 1  is a perspective drawing of the components of a preferred embodiment of a touch switch of the present invention; 
       FIG. 2  is a cross-sectional view of a two-electrode touch pad and integrated circuit chip of the present invention; 
       FIG. 3  is a plan view of an embodiment of a touch switch apparatus of the present invention; 
       FIG. 4  is an electrical schematic representation of a touch switch control circuit configured for a preferred operating mode; 
       FIG. 5  is an electrical schematic representation of a touch switch control circuit configured for an alternate preferred operating mode; 
       FIG. 6  is an electrical schematic representation of a touch switch control circuit configured for another alternate preferred operating mode; 
       FIG. 7  is an electrical schematic representation of a touch switch control circuit configured for yet another alternate preferred operating mode; 
       FIG. 8  is a cross-sectional view of an alternate embodiment of a touch pad of the present invention; 
       FIG. 9  is a cross-sectional view of another alternate embodiment of a touch pad of the present invention; and 
       FIG. 10  is a diagrammatic representation of an embodiment of a touch switch panel using a plurality of touch switches in matrixed form. 
     Similar indicia numbers in the various Figures indicate similar elements. 
   

   DESCRIPTION OF THE PREFERRED EMBODIMENTS 
   The invention pertains to a touch switch apparatus comprising a touch pad having one or more electrodes and a control circuit. Many of the drawing figures illustrating the control circuit depict the circuit as large in relation to the touch pad, for clarity. In typical applications, however, the control circuit may be small compared to the touch pad, and is preferably in the form of one or more integrated circuit chips. 
     FIG. 1  is a perspective representation of one preferred embodiment of a touch switch apparatus  20  of the present invention. Touch switch apparatus  20  comprises a touch pad  22 , a control circuit  24  comprising an integrated circuit (IC) chip  26  having eight output terminals PIN 1 -PIN 8 , and first and second resistors R 1  and R 2 . In the embodiment shown, touch pad  22  comprises a first electrode E 1  and a second electrode E 2 , although the touch pad may also be comprised of more or fewer than two electrodes. Although control circuit  24  could be fabricated using discrete electronic components, it is preferable to embody control circuit  24  in a single integrated circuit chip, such as IC chip  26 . 
   Control circuit  24 , via terminals PIN 1 -PIN 8  of IC chip  26 , is electrically coupled to, and communicates with, first and second resistors R 1  and R 2 , first and second electrodes E 1  and E 2 , and an input line  30  which is configured to supply a control and/or power signal from a remote device (not shown). Control circuit  24  also communicates with a remote device (not shown) using a first output line  32 . In some embodiments, a second output line  34  is also used for communication with the remote device (not shown). 
     FIG. 2  is a partial cross-sectional view of a typical touch switch  20  of the present invention in which the components comprising touch switch apparatus  20  are mounted on a dielectric substrate  35  having a front surface  36  and an opposing rear surface  37 . In the embodiment shown, first and second electrodes E 1  and E 2  are mounted on rear surface  37  of substrate  35 . IC chip  26  is also mounted on rear surface  37  of substrate  35 , proximate first and second electrodes E 1  and E 2 . As can be seen from both  FIGS. 1 and 2 , in the preferred embodiment it is contemplated that IC chip  26  comprising control circuit  24  be mounted in close proximity to touch pad  22 . 
   Substrate  35  is typically comprised of a relatively rigid dielectric material, such as glass, plastic, ceramic, or any other suitable dielectric material. However, substrate  35  may also comprise any other suitable dielectric material, including flexible materials. Consolidated Graphics No. HS-500, Type 561, Level 2, a 0.005 inch thick polyester material, is an example of a suitable flexible substrate. In embodiments where the touch switch apparatus components are mounted on a flexible substrate, the flexible carrier is often subsequently applied to another, generally more rigid, substrate. 
   In a preferred embodiment, substrate  35  is made of glass having a uniform thickness of about 3 mm. In other embodiments, the thickness of substrate  35  may vary, depending on the type of material used, its mechanical and electrical properties, and the physical strength and electrical sensitivity required for a particular application. The maximum functional thickness for glass and plastic substrates is on the order of several inches. However, in most practical applications, glass substrates range in thickness from about 1.1 mm to about 5 mm, while plastic substrates can be even thinner. 
   In a preferred embodiment, as shown in  FIGS. 1 and 2 , second electrode E 2  substantially surrounds first electrode E 1 . A space  28  is located between first electrode E 1  and second electrode E 2 . First electrode E 1  may be dimensioned such that it may be “covered” by a user&#39;s fingertip or other human appendage when the user touches the corresponding portion of front surface  36  of substrate  35 . In one preferred embodiment, first electrode E 1  is square and second electrode E 2  is arranged in a square pattern about and conforming to the shape of first electrode E 1 . 
   Although the touch pad geometry illustrated in  FIGS. 1 and 2  represents a preferred arrangement of first and second electrodes E 1  and E 2 , it should be recognized that the electrode arrangement may be varied extensively to accommodate a wide variety of applications. For example, the electrode size, shape, and placement may be varied to accommodate the size of the appendage or other stimulus contemplated to actuate touch switch  20 . For example, a particular application might require that a hand, rather than a finger, provide the stimulus to actuate touch switch  20 . In such an application, first and second electrodes E 1  and E 2  would be much larger and spaced farther apart. 
   First electrode E 1  may take any number of different geometric shapes, including, but not limited to, rectangles, trapezoids, circles, ellipses, triangles, hexagons, and octagons. Regardless of the shape of first electrode E 1 , second electrode E 2  can be configured to at least partially surround first electrode E 1  in a spaced-apart relationship. However, it is not necessary for second electrode E 1  to surround the first electrode even partially in order to obtain the benefits of the invention. For example, first and second electrodes E 1  and E 2  can be adjacent to each other, as shown in FIG.  3 . In alternative embodiments, second electrode E 2  may be omitted. 
   Furthermore, the electrode configuration need not be co-planar, but can be three dimensional to conform to a sphere, a cube, or other geometric shape. This design flexibility allows the invention to be used in a wide variety of applications, with substrates of varying shapes and composition. In some applications, it may not be necessary to actually touch substrate  35  upon or within which touch pad  22  and control circuit  24  are situated. For example,  FIG. 8  illustrates a touch switch apparatus  20  wherein first and second electrodes E 1  and E 2  are mounted on an exterior surface  113  of a first pane  111  of a thermopane window  110  and which can be actuated by a user bringing a suitable stimulus  115  proximate an exterior surface  114  of an opposing pane  112  of the window. 
   As noted above, first and second electrodes E 1  and E 2  need not be coplanar; they can be mounted on different sides or surfaces of a substrate, or on different substrates altogether. For example,  FIG. 9  illustrates a touch switch apparatus  20  wherein first electrode E 1  is mounted on a first surface  36  of a substrate  35  and second electrode E 2  and IC chip  26  are mounted on a second, opposing surface  37  of substrate  35 . In applications where first and second electrodes E 1  and E 2  are on the same side of a substrate, IC chip  26  can be mounted on the same side of the substrate as the electrodes, or on another side of the substrate. If the first and second electrodes are mounted on different surfaces of a substrate or on different substrates altogether, IC chip  26  can be mounted on the same surface as either of the electrodes, or on a different surface or substrate altogether. However, it is preferred that the IC chip  26  be mounted in close proximity to the electrodes. 
   Preferably, first electrode E 1  is a solid conductor. However, first electrode E 1  may also have a plurality of apertures or may have a mesh or grid pattern. In some embodiments, second electrode E 2  will take the form of a narrow ribbon partially surrounding first electrode E 2 . In other embodiments, such as where first and second electrodes E 1  and E 2  are merely adjacent each other, second electrode E 2  may also be a solid conductor or may have a mesh or grid pattern. 
   Control circuit  24  may be designed in many different ways, and it may be used with a variety of power sources, such as AC, periodically varying DC (such as a square wave), continuous DC, or others.  FIGS. 4-7  illustrate a preferred control circuit design which may be easily adapted for use with a variety of power supplies, in a variety of operating modes. The  FIG. 4  embodiment uses square wave DC power in a differential input, strobed mode of operation; the  FIG. 5  embodiment uses continuous DC power in a differential input, continuous DC mode; the FIG.  6 . embodiment uses square wave DC power in a single-ended input, strobed mode; and the  FIG. 7  embodiment uses continuous DC power in a single-ended input, continuous DC mode. 
   It is apparent from  FIGS. 4-7  that control circuit  24  can be readily adapted for various different operating modes. The foregoing four operating modes will be described in detail to demonstrate the design flexibility allowed by the invention. However, it should be recognized that the invention is by no means limited to these four operating modes. The particular operating mode and power source used in a specific application depends primarily on the requirements and specifications of the controlled device. 
   Boxed areas B 1  and B 2  on  FIGS. 4-7  indicate the demarcation between components contemplated to be located on IC chip  26  and components located off of IC chip  26 , such as electrodes E 1  and E 2 , resistors R 1  and R 2 , the controlled device (not shown), and input and output lines  30  and  32 , respectively. The portions of  FIGS. 4-7  which are outside boxed areas B 1  and B 2  are contemplated to be located on IC chip  26  and are identical for all four figures and operating modes depicted therein. 
     FIGS. 4-7  illustrate a control circuit  24  comprising a startup and bias section  40 , a pulse generator and logic section  50 , a decision circuit section  60 , and a self-holding latch section  70 , the functions of which will be described below. Each of the foregoing circuit sections  40 ,  50 ,  60  and  70  may be designed in a number of different ways, as would be known to those skilled in the art of electronic circuit design. 
   Control circuit  24  also comprises first, second, and third transistors P 1 , P 2 , and P 3 . In the embodiments described herein, transistors P 1 -P 3  are P-MOS devices, although N-MOS devices, bipolar devices, or other transistor types can also be used. Control circuit  24  further comprises an inverter I 1 , first, second, and third diodes D 1 -D 3 , first and second capacitors C 1  and C 2 , first, second, third, and fourth transistor switches SW 1 -SW 4 , and third and fourth resistors R 3  and R 4 . It should be recognized that third and resistors R 3  and R 4  may be replaced with current sources. 
   In each of the embodiments illustrated in  FIGS. 4-7 , source terminal  77  of third transistor P 3  and power input terminals  41 ,  51 ,  61 , and  71  of startup and bias section  40 , pulse generator and logic section  50 , decision circuit  60 , and self-holding latch section  70 , respectively, are electrically coupled to terminal PIN 8  of IC chip  26 . Terminal PIN 8  is in turn electrically coupled to control circuit  24  power input line  30 , which is in turn electrically coupled to a power source  25 . Typically, power source  25  is located at the controlled device (not shown). 
   A biasing output terminal  43  from startup and bias section  40  is electrically coupled to gate terminals G 2  and G 4  of second and fourth transistor switches SW 2  and SW 4 , respectively. In the preferred embodiment and as described herein, first through fourth transistor switches SW 1 -SW 4  are N-MOS devices, although other transistor types may be used, as well. 
   A power-on reset output  44  from startup and bias section  40  is electrically coupled to a power on reset input  54  at pulse generator and logic section  50 . Power on reset output  44  of startup and bias section  40  is also electrically coupled to gate terminals G 1  and G 3  of first and third transistor switches SW 1  and SW 3 . 
   Internal ground reference output  42  from the startup and bias section  40  is electrically coupled to low potential plates  102  and  103  of first and second capacitors C 1  and C 2 , source terminals S 1 , S 2 , S 3 , and S 4  of first through fourth transistor switches SW 1 -SW 4 , respectively, internal ground reference output  52  of the pulse generator and logic section  50 , internal ground reference output  62  of decision circuit  60 , anode  98  of third diode D 3 , low potential ends  96  and  97  of third and fourth resistors R 3  and R 4 , and to terminal PIN 6  of IC chip  26 . The node thus described will hereinafter sometimes be referred to as the internal ground reference CHIP VSS. 
   A pulse output  53  from pulse generator and logic section output  50  is electrically coupled to source terminals  80  and  81  of first and second transistors P 1  and P 2 , respectively, and to terminal PIN 2  of IC  26 . Gate terminal  82  of first transistor P 1  is electrically coupled to terminal PIN 1  of IC  26 . Gate terminal  83  of second transistor P 2  is electrically coupled to terminal PIN 3  of IC  26 . 
   Drain terminal  84  of first transistor P 1  is electrically coupled to anode  90  of first diode D 1  and to high potential end  94  of third resistor R 3 . Drain terminal  85  of second transistor P 2  is electrically coupled to anode  91  of second diode D 2  and to high potential end  95  of fourth resistor R 4 . 
   Cathode  92  of first diode D 1  is electrically coupled to PLUS input terminal  64  of decision circuit  60 , to drain terminals  86  and  87  of first and second transistor switches SW 1  and SW 2 , and to high potential plate  100  of first capacitor C 1 . Cathode  93  of second diode D 2  is electrically coupled to MINUS input terminal  66  of decision circuit  60 , to drain terminals  88  and  89  of third and fourth transistor switches SW 3  and SW 4 , and to high potential plate  101  of second capacitor C 2 . 
   Logic output  63  of decision circuit  60  is electrically coupled to input  75  of inverter I 1  and to latch trigger input  73  of self-holding latch section  70 . Output  72  of self-holding latch section  70  is electrically coupled to terminal PIN 4  of IC  26 . 
   In the illustrated embodiments, decision circuit section  60  is designed so that its output  63  is at a low potential when its PLUS and MINUS inputs  64  and  66 , respectively, are at substantially equal potentials or when MINUS input  66  is at a substantially higher potential than PLUS input  64 . Decision circuit section  60  output  63  is at a high potential only when PLUS input  64  is at a substantially higher potential than MINUS input  66 . 
   Self-holding latch section  70  is designed so that no current flows through latch section  70  from the control circuit  24  power supply  25  to internal ground reference CHIP VSS and through third diode D 3  when decision circuit section  60  logic output  63  is at a low potential. However, when decision circuit  60  section logic output  63  is at a high potential, latch trigger input  73  is at a high potential, thus triggering latch circuit  70  and enabling current to flow through latch section  70  from control circuit  24  power supply  25  to internal ground reference CHIP VSS and through third diode D 3 , by way of latch  70  power input and output terminals  71  and  72 , respectively. Once latch  70  has been triggered, it remains triggered, or sealed in, until power is removed from control circuit  24 . The design and construction of a latch section which operates in this manner is known to those skilled in the art and need not be described in detail herein. 
   Output terminal  76  of inverter I 1  is electrically coupled to gate terminal  78  of third transistor P 3 . Drain terminal  79  of third transistor P 3  is electrically coupled to terminal PIN 7  of IC  26 . 
   Third diode D 3  is provided to prevent back-biasing of control circuit  24  when touch switch apparatus  20  is used in multiplexed applications. It can be omitted in applications where only a single touch pad  22  is used, or where multiple touch pads  22  are used, but not multiplexed. 
   The foregoing description of the basic design of control circuit  24  is identical for each of the four operating modes depicted in  FIGS. 4-7 . The distinctions in overall apparatus configuration among the four operating modes lie primarily in the external terminal connections of IC  26 , as will be described in detail below. 
     FIG. 4  illustrates a touch switch apparatus  20  configured for operation in differential input strobed mode, as described below. Control circuit  24  for operation in this mode is configured as described hereinabove for  FIGS. 4-7  generally. Terminal PIN 2  of IC  26  is electrically coupled to high potential ends  104  and  105  of first and second resistors R 1  and R 2 , respectively. Terminal PIN 1  of IC  26  is electrically coupled to both low potential end  106  of first resistor R 1  and to first electrode E 1 . Terminal PIN 3  of IC  26  is electrically coupled to both low potential end  107  of second resistor R 2  and to second electrode E 2 . 
   The circuit elements represented as C 3  and C 4  in  FIGS. 4-7  are not discrete electrical components. Rather, reference characters C 3  and C 4  represent the capacitance-to-ground of first and second electrodes E 1  and E 2 , respectively. 
   Terminal PIN 8  of IC  26  is electrically coupled to input line  30 , which is in turn electrically coupled to a power signal source  25  at, for example, the controlled device (not shown). Terminal PIN 4  of IC  26  is electrically coupled to terminal PIN 6  of IC  26 , thereby electrically coupling output terminal  72  of latch  70  to the internal ground reference CHIP VSS and anode  98  of third diode D 3 . Terminal PIN 7  of IC chip  26  is not externally terminated in this embodiment. Terminal PIN 5  of IC  26  is electrically coupled to output line  32 , which is in turn electrically coupled to high potential end  108  of fifth resistor R 5  and to output line  120 , which is connected to the controlled device (not shown), either directly or by way of a processor or other intermediate device (not shown). Low potential end  109  of resistor R 5  is electrically coupled to the system ground. In a typical application, resistor R 5  will be at a substantial distance from the other components comprising touch switch apparatus  20 . That is, in the preferred embodiment, resistor R 5  is contemplated not to be near touch pad  22  and control circuit  24 . 
     FIG. 5  illustrates a typical touch switch control circuit  24  configured for operation in differential input continuous DC mode, as described below. The overall control circuit and apparatus is identical to that described for  FIG. 4  hereinabove, with three exceptions. First, in the  FIG. 5  embodiment, terminal PIN 7  of IC  26  is electrically coupled to high potential end  108  of resistor R 5  and to output line  120 , which is connected to the controlled device (not shown) either directly or by way of a processor or other intermediate device (not shown), whereas terminal PIN 7  is not externally terminated in the  FIG. 4  embodiment. Second, in the  FIG. 5  embodiment, terminals PIN 4  and PIN 6  of IC  26  are not electrically coupled to each other or otherwise externally terminated, whereas they are in the  FIG. 4  embodiment. Third, in the  FIG. 5  embodiment, terminal PIN 5  of IC  26  is electrically coupled to low potential end  109  of resistor R 5 , whereas in the  FIG. 4  embodiment, terminal PIN 5  of IC  26  is electrically coupled to high potential end  108  of fifth resistor and to the controlled device (not shown). As in the  FIG. 4  embodiment, fifth resistor R 5  will typically be at a substantial distance from the other components comprising touch switch apparatus  20 . 
     FIG. 6  illustrates a typical touch switch control circuit configured for operation in single-ended input strobed mode, as described below. Control circuit  24  is configured as described hereinabove for  FIGS. 4-7  generally. Terminal PIN 2  of IC  26  is electrically coupled to high potential ends  104  and  105  of first and second resistors R 1  and R 2 , respectively. Terminal PIN 1  of IC  26  is electrically coupled to both low potential end  106  of first resistor R 1  and to first electrode E 1 . Terminal PIN 3  of IC  26  is electrically coupled to both low potential end  107  of second resistor R 2  and to high potential end  110  of sixth resistor electrode R 6 , such that second resistor R 2  and sixth resistor R 6  form a voltage divider. Low potential end  111  of sixth resistor R 6  is electrically coupled to internal ground reference CHIP VSS, typically at a point proximate terminal PIN 5  of IC  26 . In  FIG. 6 , the electrical connection of sixth resistor R 6  to the internal ground reference CHIP VSS is represented by broken line “A—A” for clarity. 
   Terminal PIN 8  of IC  26  is electrically coupled to input line  30 , which is in turn electrically coupled to a power signal source  25 . Terminal PIN 5  of IC  26  is electrically coupled to output line  32 , which is in turn electrically coupled to high potential end  108  of fifth resistor R 5  and to output line  120 . Output line  120  is electrically coupled to the controlled device (not shown), either directly or by way of a processor or other intermediate device. Terminal PIN 4  of IC  26  is electrically coupled to terminal PIN 6  of IC  26 . Terminal PIN  7  of IC  26  is not externally terminated in this embodiment. In a typical application, fifth resistor R 5  will be at a substantial distance from the other components comprising touch switch apparatus  20 . 
     FIG. 7  illustrates a typical touch switch control circuit configured for operation in single ended input continuous DC mode, as described below. Control circuit  24  is configured as described hereinabove for  FIGS. 4-7  generally. The overall control circuit and apparatus is identical to that described for  FIG. 6  hereinabove, with three exceptions. First, in the  FIG. 7  embodiment, terminal PIN 7  of IC  26  is electrically coupled to high potential end  108  of fifth resistor R 5  and to output line  120 , which is in turn connected to the controlled device (not shown), typically by way of a microprocessor or other controller (not shown). Terminal PIN 7  of IC  26  is not externally terminated in the  FIG. 6  embodiment. Second, in the  FIG. 7  embodiment, terminals PIN 4  and PIN 6  of IC  26  are not electrically coupled or otherwise externally terminated, whereas they are in the  FIG. 6  embodiment. Third, in the  FIG. 7  embodiment, terminal PIN 5  of IC  26  is electrically coupled to low potential end  109  of fifth resistor R 5 , whereas in the  FIG. 6  embodiment, terminal PIN 5  of IC  26  is electrically coupled to high potential end  108  of fifth resistor and to output line  120 . In a typical application, fifth resistor R 5  will be at a substantial distance from the other components comprising touch switch apparatus  20 . In  FIG. 7 , the electrical connection of sixth resistor R 6  to the internal ground reference CHIP VSS is represented by broken line “A—A” for clarity. 
   A touch switch apparatus  20  configured for the differential input strobed mode operates as follows. Referring to  FIG. 4 , a power/control signal  25  is provided to terminal PIN 8  of IC  26  and, in turn, to power input terminals  41 ,  51 ,  61 , and  71  of start up and bias section  40 , pulse generator and logic section  50 , decision circuit section  60 ; and self-holding latch section  70 , respectively. 
   Upon becoming powered, and after a suitable delay interval to allow for stabilization (approximately 200 microseconds is sufficient), start up and bias section  40  outputs a short duration power-on reset signal from output terminal  44  to gate terminals G 1  and G 3  of first transistor switch SW 1  and third transistor switch SW 3 , respectively, causing first and third transistor switches SW 1  and SW 3  to turn on, and thus providing a current path from high potential plates  100  and  101  of first and second capacitors C 1  and C 2 , respectively, to the internal ground reference CHIP VSS. The power on reset signal duration is sufficient to allow any charge present on first and second capacitors C 1  and C 2  to be substantially completely discharged to the internal ground reference CHIP VSS. In this manner, PLUS and MINUS inputs  64  and  66  to decision circuit section  60  attain an initial low-potential state. 
   At substantially the same time, start up and bias circuit  40  sends a power on reset signal from output  44  to input  54  of pulse generator and logic section  50 , thus initializing it. After a suitable delay to allow pulse generator and logic section  50  to stabilize, pulse generator and logic section  50  generates a pulse and outputs it from pulse output terminal  53  to first and second electrodes E 1  and E 2  by way of first and second resistors R 1  and R 2 , and to source terminals  80  and  81  of first and second transistors P 1  and P 2 , respectively. The pulse may be of any suitable waveform, such as a square wave pulse. 
   Startup and bias circuit  40  also outputs a bias voltage from bias output  43  to gate terminals G 2  and G 4  of second and fourth transistor switches SW 2  and SW 4 , respectively. The bias voltage is out of phase with the pulse output to first and second electrodes E 1  and E 2 . That is, when the pulse output is at a high state, the bias voltage output is at a low state and when the pulse output is at a low state, the bias voltage output is at a high state. 
   When a pulse is applied to first and second electrodes E 1  and E 2  through first and second resistors R 1  and R 2 , respectively, the voltage at gate terminals  82  and  83  of first and second transistors P 1  and P 2  is initially at a lower potential than that at source terminals  80  and  81  of first and second transistors P 1  and P 2 , respectively, thus biasing first and second transistors P 1  and P 2  and causing them to turn on. With first and second transistors P 1  and P 2  turned on, current will flow through third and fourth resistors R 3  and R 4 , thus creating a peak potential at anode terminals  90  and  91  of first and second diodes D 1  and D 2 , respectively. 
   If the peak potential at anodes  90  and  91  of first and second diodes D 1  and D 2  is higher than the potential across first and second capacitors C 1  and C 2 , a peak current is established through first and second diodes D 1  and D 2 , causing first and second capacitors C 1  and C 2  to become charged, and establishing a peak potential at each of PLUS and MINUS inputs  64  and  66  to decision circuit section  60 . This situation will occur, for example, following the first pulse after control circuit  24  has been initialized because first and second capacitors C 1  and C 2  will have become discharged upon startup, as described above. 
   As is evident to one skilled in the art, the biasing of first and second transistors P 1  and P 2 , the current through third and fourth resistors R 3  and R 4 , the peak potential created at anodes  90  and  91  of first and second diodes D 1  and D 2 , and the peak potential created at each of PLUS and MINUS inputs  64  and  66  to decision circuit  60  are proportional to the condition of the electric field at first and second electrodes E 1  and E 2 . The condition of the electric field proximate electrodes E 1  and E 2  will vary in response to stimuli present proximate the electrodes. 
   With control circuit  24  activated, as described above, and with no stimuli present proximate either first and second electrodes E 1  and E 2 , the potentials at each of PLUS and MINUS inputs  64  and  66  to decision circuit  60  are in what may be termed a neutral state. In the neutral state, the potentials at each of PLUS and MINUS inputs  64  and  66  may be substantially equal. However, in order to prevent unintended actuations, it may be desirable to adjust control circuit  24  so that the neutral state of MINUS input  66  is at a somewhat higher potential than the neutral state of PLUS input  64 . This adjustment may be effected by varying the configurations of first and second electrodes E 1  and E 2  and the values of first and second resistors R 1  and R 2  to achieve the desired neutral state potentials. Regardless of the neutral state potentials, it is contemplated that decision circuit  60  output  63  will be at a low potential unless PLUS input  64  is at a substantially higher potential than MINUS input  66 . 
   With decision circuit  60  output  63  at a low potential, inverter I 1  causes the potential at gate terminal  78  of third transistor P 3  to be at a high level, substantially equal to the potential at source terminal  77 . In this state, third transistor P 3  is not biased and will remain turned off. However, in this embodiment, terminal PIN 7  of IC  26  is not terminated. Drain terminal  79  of third transistor P 3  is therefore in an open-circuit condition, and the state of third transistor P 3  is of no consequence to the function of the apparatus. Also, with decision circuit  60  output  63 , and consequently latch trigger input  73 , at a low state, self holding latch circuit  70  will not be triggered, and no current will flow through latch  70  from power supply  25  to the internal ground reference CHIP VSS and through third diode D 3 . 
   Over a period of time which is determined by the pulse voltage, the values of first and second resistors R 1  and R 2 , and the capacitance to ground of first and second electrodes E 1  and E 2  (represented in the figures as virtual capacitors C 3  and C 4 ), the potential at first and second electrodes E 1  and E 2  eventually rises to substantially equal the pulse voltage and thus the voltage at source terminals  80  and  81  of first and second transistors P 1  and P 2 , thus unbiasing first and second transistors P 1  and P 2 . When this state is reached, first and second transistors P 1  and P 2  turn off, and the potentials at anodes  90  and  91  of first and second diodes D 1  and D 2  begin to decrease at a substantially equal rate towards the internal ground reference CHIP VSS level. Eventually, the anode potential at each of first and second diodes D 1  and D 2  is likely to fall below the respective cathode potential. At this point, diodes D 1  and D 2  become reverse biased and prevent first and second capacitors C 1  and C 2  from discharging. 
   When the pulse on output  53  goes to a low state, the bias voltage output goes to a high state relative to the internal ground reference CHIP VSS, and applies the elevated bias voltage to gate terminals G 2  and G 4  of second and fourth transistor switches SW 2  and SW 4 . In this state, second and fourth transistor switches SW 2  and SW 4  become slightly biased and turn on sufficiently to effect a slow, controlled discharge of first and second capacitors C 1  and C 2  to the internal ground reference CHIP VSS. When the pulse next goes to a high state, the bias voltage will return to a low state, second and fourth transistor switches SW 2  and SW 4  will turn off, and the circuit will respond as described initially. 
   If a stimulus is present at or near second electrode E 2  when the pulse from pulse generator and logic section  50  goes to a high potential, first transistor P 1  will operate as described hereinabove. That is, first transistor P 1  will be initially biased and will allow some current to flow through third resistor R 3 , creating a peak potential at anode  90  of first diode D 1 , and allowing a peak current to flow through first diode D 1 , thereby charging first capacitor C 1 , and establishing a peak potential at PLUS input  64  to decision circuit  60 . Once the voltage at first electrode E 1  has stabilized in response to the incoming pulse, first transistor P 1  will become unbiased and will turn off. 
   Second transistor P 2  operates in much the same way, except that the presence of the stimulus proximate second electrode E 2  will alter the RC time constant for that circuit segment, thus lengthening the time required for the potential at second electrode E 2  to stabilize. As a consequence, second transistor P 2  will remain biased on for a longer period of time than first transistor P 1 , allowing a greater peak current to flow through fourth resistor R 4  than flows through third resistor R 3 , thus generating a peak potential at anode  91  of second diode D 2  which is greater than the peak potential present at anode  90  of first diode D 1 . Consequently, a peak current will flow through second diode D 2 , causing second capacitor C 2  to become charged, ultimately resulting in a peak potential at MINUS input  66  to decision circuit  60  which is greater than the peak potential at PLUS input  64  to decision circuit. Since decision circuit  60  is configured so that its output will be at a low potential when the potential at MINUS input  66  is greater than or substantially equal to the potential at the PLUS input  64 , decision circuit  60  output terminal  63  will be at a low potential. 
   With decision circuit  60  output terminal  63 , and consequently latch trigger input terminal  73 , at a low potential, self holding latch  70  will not be triggered. Inverter  11  and third transistor P 3  will operated as described previously, although, again, the state of third transistor P 3  is inconsequential in this configuration. 
   In the event that a contaminant or foreign object, or other stimulus, substantially covers, or is applied to, both first and second electrodes E 1  and E 2 , the system will respond much in the same way as it would when no stimulus is present at either the first electrode or second electrode. However, with contaminants or a foreign object present proximate both electrodes E 1  and E 2 , the RC time constant for those segments of the circuit will be altered such that it will take longer for the voltage at both first and second electrodes E 1  and E 2 , respectively, to substantially equalize with the pulse voltage. Consequently, both first and second transistors P 1  and P 2  will turn on and will allow more current to flow through third and fourth resistors R 3  and R 4  than they would in a condition where neither first nor the second electrode E 1  or E 2  is affected by a stimulus. However, first and second transistors P 1  and P 2  will be substantially equally biased. Therefore, a substantially equal peak potential will be developed at anodes  90  and  91  of both first and second diodes D 1  and D 2 , causing a substantially equal peak current to flow through first and second diodes D 1  and D 2 , charging first and second capacitors C 1  and C 2 , and establishing a substantially equal peak potential at both PLUS and MINUS inputs  64  and  66  to decision circuit  60 . In this state, decision circuit section  60  output terminal  63  will be at a low potential, latch trigger input terminal  73  of self holding latch  70  will be at a low potential, and latch  70  will remain untriggered. As previously described, the state of inverter I 1  and third transistor P 3  is inconsequential in this embodiment. 
   In the situation where a stimulus is applied proximate first electrode E 1 , but not second electrode, second transistor P 2  will be initially biased and will turn on, establishing a current through fourth resistor R 4 , and generating a peak potential at anode terminal  90  of second diode D 2 . A peak current will flow through second diode D 2 , charging second capacitor C 2 , and establishing a peak potential at MINUS input  66  of decision circuit section  60 . As the voltage at gate terminal  81  of second transistor P 2  rises to the level of the pulse voltage, second transistor P 2  will become unbiased and will turn off. Second diode D 2  will then become reverse biased, and will prevent second capacitor C 2  from discharging. 
   As is evident to one skilled in the art, the presence of a stimulus proximate first electrode E 1  will lengthen the time required for the potential at first electrode E 1  to stabilize. As a consequence, first transistor P 1  will remain biased on for a longer period of time than second transistor P 2 , allowing a greater peak current to flow through third resistor R 3  than through fourth resistor R 4 , thus generating a peak potential at anode  90  of first diode D 1  which is greater than the potential present at anode  91  of second diode D 2 . Consequently, a peak current of greater magnitude and/or duration will flow through first diode D 1  than through second diode D 2 , causing first capacitor C 1  to become charged, ultimately resulting in a peak potential at PLUS input  64  to decision circuit  60  which is substantially greater than the peak potential at MINUS input  66  to decision circuit  60 . Since decision circuit  60  is configured so that output terminal  63  will be at a high state when the potential at PLUS input  64  is greater than the potential at MINUS input  66 , decision circuit  60  output  63  will be at a high potential. 
   With decision circuit  60  output  63  at a high potential, inverter I 1  will cause potential at gate terminal  78  of third transistor P 3  to be low relative to the potential at source terminal  77 , thus biasing third transistor P 3 , and causing it to turn on. However, since terminal PIN 7  of IC  26  is not terminated in this embodiment, the state of third transistor P 3  is of no consequence. 
   With decision circuit  60  output terminal  63  at a high potential, self holding latch circuit  70  trigger input terminal  73  will also be at a high potential, thus triggering latch  70 . When self holding latch  70  is triggered, a current path is established from power supply  25  to internal ground reference CHIP VSS and through third diode D 3 , effectively short circuiting the remainder of control circuit  24 , including startup and bias section  40 , pulse generator and logic section  50 , and decision circuit section  60 . In this state, those sections of control circuit  24  become substantially de-energized and cease to function. 
   Once triggered, self holding latch  70  will remain triggered, regardless of the subsequent state of stimuli proximate either or both of electrodes E 1  and E 2 . Latch  70  will reset when the power from the power supply  25  goes to a near zero state, such as when the square wave strobe signal from power supply  25  of this example falls to zero. 
   While self holding latch  70  is in the triggered state, a steady state signal will be supplied through fifth resistor R 5  and back to the controlled device (not shown). In this manner, touch switch apparatus  20  emulates the change of state associated with a maintained-contact mechanical switch. 
   Referring now to  FIG. 5 , the operation of a touch switch apparatus  20  configured for the differential input continuous DC mode is as follows. The control circuit  24 , up to and including decision circuit  60 , performs in substantially the same manner as when configured for the differential input strobed mode of operation, as described above with reference to FIG.  4 . That is, with no stimulus present proximate either first or second electrodes E 1  and E 2 , with a stimulus present proximate both first and second electrodes E 1  and E 2 , or with a stimulus present proximate second electrode E 2 , but not first electrode E 1 , the decision circuit  60  output  63  will be at a low potential. With a stimulus present proximate first electrode E 1 , but not second electrode E 2 , the decision circuit  60  output  63  will be at a high level. 
   As can be readily seen in  FIG. 5 , self holding latch circuit  70  output  72  is not terminated in this embodiment, and the self holding latch  70  is therefore inoperative in differential input DC mode. However, drain terminal  79  of third transistor P 3  is electrically coupled to internal ground reference CHIP VSS and to output line  32  in this embodiment, and it therefore becomes an operative part of control circuit  24 . When decision circuit  60  output  63  is at a low potential, inverter I 1  causes the potential at gate terminal  78  of third transistor P 3  to be at a high potential, substantially equal to the potential source terminal  77 . In this state, third transistor P 3  is not biased and does not turn on. When decision circuit  60  output  63  is at a high potential, inverter I 1  causes the potential at gate terminal  78  of third transistor P 3  to be at a low potential compared to the potential at source terminal  77 . In this state, third transistor P 3  is biased and turns on, allowing current to be established through third transistor P 3  and fifth resistor R 5 . Output line resistor R 5  limits the current through third transistor P 3  such that the balance of control circuit  24  is not short circuited and remains operative. 
   In the DC mode shown in  FIG. 5 , control circuit  24  also responds to the removal of the stimulus from the proximity of first electrode E 1 . So long as a stimulus remains present proximate first electrode E 1 , but not second electrode E 2 , each time the pulse goes to a high state, a peak potential will be created at anode  90  of first diode D 1  which is higher than the peak potential at anode  91  of second diode D 2 . Consequently, the peak potential at PLUS input  64  to decision circuit  60  will be at a higher level than the peak potential at MINUS input  66  and control circuit  24  will behave as described above. When the stimulus is removed, however, and no stimulus is present proximate either first electrode E 1  or second electrode E 2 , the charge on first capacitor C 1  will eventually discharge to a neutral state by means of the biasing function of second transistor switch SW 2 . At this point, the potential at PLUS input  64  of decision circuit  60  will no longer be higher or substantially higher than the potential at MINUS input  66 , and decision circuit  60  output  63  will return to a low state. 
   In this manner, touch switch apparatus  20  operating in differential input DC mode emulates a momentary contact, push-to-close and release-to-open, mechanical switch. It should be recognized that, with minor revisions, the control circuit could be configured to emulate a push-to-open and release-to-close mechanical switch. 
   Referring now to  FIG. 6 , touch switch apparatus  20  configured for the single ended input strobed mode of operation operates as follows. When a pulse is applied to first electrode E 1  and first and second resistors R 1  and R 2 , current flows through second resistor R 2  and sixth resistor R 6 . Second and sixth resistors R 2  and R 6  are configured as a voltage divider; that is, when the pulse output is in a high state, gate terminal  83  of second transistor P 2  will be at a lower potential than source terminal  81  of second transistor P 2 . Therefore, when pulse output  53  is in a high state, second transistor P 2  will be continuously biased and will allow a constant current to flow through fourth resistor R 4 , thus creating a reference potential at anode  91  of second diode D 2 . The reference potential at anode  91  of second diode D 2  will establish a current through second diode D 2 , causing second capacitor C 2  to become charged, and thus creating a reference potential at MINUS input  66  to decision circuit  60 . When the reference potential at MINUS input  66  becomes substantially equal to the reference potential at anode  91  of second diode D 2 , the current through second diode D 2  will cease. 
   Concurrently, with no stimulus present at first electrode E 1 , the pulse applied to source terminal  80  of first transistor P 1  and to first electrode E 1  will initially cause first transistor P 1  to become biased and to turn on. A current will thus be established through third resistor R 3  and a peak potential will be created at anode  90  of first diode D 1 . The peak potential will establish a peak current through first diode D 1 , charging first capacitor C 1  and creating a peak potential at PLUS input  64  of the decision circuit. Resistors R 1 , R 2 , R 3 , R 4 , and R 6  are selected so that when no stimulus is present proximate first electrode E 1 , the reference potential at MINUS input  66  of decision circuit  60  will be greater than or equal to the peak potential at to PLUS terminal  64  of decision circuit  60 . 
   In this state, output  63  of the decision circuit  60  will be at a low potential and self holding latch  70  will not be triggered. Also, inverter I 1  will cause the potential at gate terminal  78  of third transistor P 3  to be at a high state, substantially equal to the source terminal  77  potential, so that third transistor P 3  is unbiased and remains turned off. However, this is of no consequence since drain terminal  79  of third transistor P 3  is in an open-circuit condition in this embodiment. 
   This embodiment does not require a second electrode, although a two-electrode touch pad may be adapted for use in this mode. In the event a two-electrode touch pad is adapted for use in this mode of operation, the presence or absence of a stimulus proximate the second electrode has no effect on the operation of the circuit. 
   In the event that a stimulus is present proximate first electrode E 1 , the operation of second transistor P 2  is the same as described hereinabove for this embodiment. However, the presence of the stimulus proximate first electrode E 1  will cause a greater time to be required for the voltage at gate terminal  82  of first transistor P 1  to become equalized with source terminal  80  potential at first transistor. Consequently, first transistor P 1  will be turned on and will allow a relatively greater current to flow through third resistor R 3 , compared to the current that second transistor P 2  allows to flow through fourth resistor R 4 . As a result, the peak potential at anode  90  of first diode D 1  will be greater than the reference potential at anode  91  of second diode D 2 . As a result, the peak potential at PLUS input  64  of decision circuit  60  will be greater than the reference potential at MINUS input  66  of decision circuit  60 , and output  63  from decision circuit  60  will therefore be at a high state. With output  63  of decision circuit  60  at a high state, inverter I 1  causes the potential at gate terminal  78  of third transistor P 3  to be at a low state, thus turning transistor P 3  on. However, since drain terminal  79  of third transistor P 3  is effectively not terminated, this is of no consequence. 
   With output  63  of decision circuit  60  at a high state, latch trigger input  73  is at a high state, and self holding latch  70  is triggered, thus establishing a current path through latch section  70 , from power supply  25  to internal ground reference CHIP VSS and through third diode D 3 , thereby effectively short circuiting the balance of control circuit  24 . Self holding latch  70  will remain in this state until power to latch input terminal  71  is removed. Until latch  70  is thus reset, a continuous digital control signal is output to the controlled device (not shown). In this manner, touch switch apparatus  20  emulates a change of state associated with a mechanical switch. 
   Referring now the  FIG. 7 , a touch switch apparatus  20  configured for operation in the single ended input continuous DC mode operates as follows. The operation and functionality of control circuit  24  is substantially the same as described for the single ended input, strobed mode as described hereinabove with reference to FIG.  6 . However, in the single ended input, DC mode, self holding latch output  72  is open circuited and self holding latch  70  is therefore not operative. 
   With no stimulus applied to first electrode E 1 , output  63  of decision circuit  60  is at a low potential. Consequently, inverter I 1  output  76  to gate terminal  78  of third transistor P 3  is at a high potential. With gate terminal  78  of third transistor P 3  at a high potential, similar to the potential at source terminal  77 , third transistor P 3  is unbiased and does not turn on, and therefore no current flows through third transistor P 3  or through fifth resistor R 5 . 
   With a stimulus proximate first electrode E 1 , output  63  of decision circuit  60 , and consequently input  75  to inverter I 1 , is at a high state. Inverter  11  changes the high level input to a low level output, and provides output  76  to gate terminal  78  potential of third transistor P 3 . With gate terminal  78  at a low potential compared to source terminal  77 , third transistor P 3  is biased, it turns on, and current flows through third transistor P 3  and fifth resistor R 5 . This creates an elevated potential at anode  108  of fifth resistor R 5  which may be used as an input to the controlled device (not shown) via output line  120 . 
   In the continuous DC mode of  FIG. 7 , the control circuit responds to the removal of the stimulus from the proximity of first electrode E 1 . So long as the stimulus remains present proximate first electrode E 1 , each time the pulse goes to a high state, a peak potential will be created at anode  90  of first diode D 1  which is higher than the reference potential at anode  91  of second diode D 2 . Consequently, the peak potential at PLUS input  64  to the decision circuit  60  will be at a higher level than the reference potential at the MINUS input  66  and control circuit  24  will behave as described above. When the stimulus is removed from first electrode E 1 , the charge on first capacitor C 1  will eventually discharge to a neutral state by means of the biasing function of second transistor switch SW 2 . At this point, the peak potential at PLUS input  64  of decision circuit  60  will no longer be higher or substantially higher than the reference potential at MINUS input  66 , and decision circuit  60  output  63  will return to a low state. 
   In this manner, touch switch apparatus  20  operating in single-ended input DC mode emulates a momentary contact mechanical switch. With minor revisions, the control circuit could be configured to emulate a push-to-open and release-to-close mechanical switch. 
   Thus far, this specification has described the physical construction and operation of a single touch switch. Typical touch switch applications frequently involve a plurality of touch switches which are used to effect control over a device.  FIG. 10  shows a switch panel comprising nine touch switches  20 , where the nine touch switches  20  are arranged in a three-by-three matrix. Box B 3  represents components at the touch panel, while box B 4  represents components at the controlled device. Although any number of touch switches could theoretically be laid out in any manner, matrix layouts such as this one are readily multiplexable, reducing the number of necessary input and output lines from the controlled device, and are preferred. 
   While several embodiments of the present invention have been shown, it will be obvious to those skilled in the art that numerous modifications may be made without departing from the spirit of the claims appended hereto.