Abstract:
A technique for voltage regulation involves switching between light load mode and PWM mode based on load conditions. Advantageously, this improves efficiency at light load. In an embodiment, error amplifier output is used to determine whether load is light. When light load is detected, extend PWM off time until the output voltage reaches a load threshold.

Description:
CROSS-REFERENCE TO RELATED APPLICATIONS  
       [0001]     This Application claims the benefit of U.S. Provisional Application No. 60/605,462 filed Aug. 30, 2004, which is incorporated by reference. 
     
    
     BACKGROUND  
       [0002]     The advent of portable electronics and the need for longer battery life calls for new types of voltage regulators, which are very efficient in both low current and high current load conditions. For example, handheld devices such as PDA and cell phones can benefit from high efficiency in both standby and active modes to extend battery life. A very low amount of operating current is of particular importance in standby mode because the devices run in this mode most of the time.  
         [0003]     A pulse width modulated (PWM) switching regulator is an efficient regulation scheme during heavy loads. PWM switching regulators offer high efficiency, low output voltage ripple, and good line and load regulation. However, at light loads the PWM regulator has poor efficiency because switching frequency related losses, such as FET switching loss, core loss, gate-drive loss, etc., are not concomitant with decreased output current due to unchanged switching frequency.  
         [0004]     Efforts have been made to improve light load efficiency of switching regulators. One method is to operate the switching regulator intermittently based on load demand with fixed peak inductor current. Unfortunately, despite improved light load efficiency, this scheme inherently has a large output ripple voltage.  
       SUMMARY  
       [0005]     The following embodiments and aspects thereof are described and illustrated in conjunction with systems, tools, and methods that are meant to be exemplary and illustrative, not limiting in scope. In various embodiments, one or more of the above-described problems have been reduced or eliminated, while other embodiments are directed to other improvements.  
         [0006]     A technique for voltage regulation involves switching between light load mode and PWM mode based on load conditions. Advantageously, this improves efficiency at light load. In an embodiment, error amplifier output is used to determine whether load is light because this signal is a good indicator of load conditions. When light load is detected, extend PWM off time until the output voltage reaches a load threshold.  
         [0007]     The proposed circuits can offer, among other advantages, increasing battery lifetime, improved efficiency, or decreased loss. These and other advantages of the present invention will become apparent to those skilled in the art upon a reading of the following descriptions and a study of the several figures of the drawings.  
     
    
     BRIEF DESCRIPTION OF THE DRAWINGS  
       [0008]     Embodiments of the invention are illustrated in the figures. However, the embodiments and figures are illustrative rather than limiting; they provide examples of the invention.  
         [0009]      FIGS. 1A and 1B  depict examples of systems with a dual mode switching regulator module.  
         [0010]      FIG. 2  depicts an example of various signals that may be generated by the system of  FIG. 1 .  
         [0011]      FIG. 3  depicts an alternative example of a system with a dual mode switching regulator module.  
         [0012]      FIG. 4  depicts an alternative example of a system with a dual mode switching regulator module.  
         [0013]      FIG. 5  depicts an alternative example of a system with a dual mode switching regulator module.  
     
    
     DETAILED DESCRIPTION OF THE INVENTION  
       [0014]     In the following description, several specific details are presented to provide a thorough understanding of embodiments of the invention. One skilled in the relevant art will recognize, however, that the invention can be practiced without one or more of the specific details, or in combination with other methods, components, materials etc. In other instances, well-known structures, materials, implementations or operations are not shown or described in detail to avoid obscuring aspects of various embodiments of the invention.  
         [0015]      FIGS. 1A and 1B  depict examples of systems  100 A and  100 B, respectively, with a dual mode switching regulator module.  
         [0016]      FIG. 1A  depicts an example of a system  100  with a dual mode switching regulator module. The system  100  includes a switching regulator  102 , an error amplifier  104 , a pulse frequency modulated (PFM) comparator  106 , and a PWM control circuit  120 . In the example of  FIG. 1B , the PWM control circuit  120  includes an oscillator  108 , a pulse width modulated (PWM) comparator  110 , and a PWM latch  112 . The systems  100 A and  100 B may be referred to collectively as the system  100 . The components of the control circuit  120  are described below, but it should be noted that the PWM control circuit  120  can have a number of different implementations. The PWM control circuit  120  is not limited to the PWM control circuit  120  shown in the example of  FIG. 1B . However, solely for the purposes of illustrative simplicity, the system  100  is treated as if the PWM control circuit  120  includes the components depicted in  FIG. 1B . One of skill in the relevant art would understand that other implementations of the PWM control circuit  120  are possible.  
         [0017]     In the example of  FIG. 1B , depicted resistors are part of an RC network. The RC network behaves in a manner that one of skill in the art would understand. The resistors may be referred to as feedback resistors (the resistor coupled between an input of the error amplifier  104  and an output of the error amplifier  104  may be referred to as a compensation RC network resistor).  
         [0018]     In the example of  FIG. 1B , the switching regulator  102  has a voltage input (Vin) and a voltage output (Vout), and is coupled to the error amplifier  104  and the PWM latch  112 . The error amplifier  104  feedbacks the output voltage through a series-parallel combination of resistors and capacitors. One or more of the resistors are optional, depending upon the implementation. A series-parallel combination of resistors and capacitors compensates the feedback loop stability and dynamics. The error amplifier  104  has the Vout input, a voltage reference (Vref) input, and an output signal. The error amplifier  104  output is coupled to the PFM comparator  106  and the PWM comparator  110 .  
         [0019]     In the example of  FIG. 1B , the PFM comparator  106  has a PFM threshold voltage input, along with the output of the error amplifier  104 , and a command signal (Toff) to extend off time of a clock signal. The output of the PFM comparator  106  is coupled to the oscillator  108 . The oscillator  108  has a ramp signal output and a clock (Clk) signal output. The ramp signal output is coupled to the PWM comparator  110 , along with the output of the error amplifier. The Clk signal is coupled to the PWM latch  112 , along with output of the PWM comparator  110 . The output of the PWM latch  112  is a PWM signal that is coupled to the switching network  102 . The latch  112  may be implemented as any switching component such as, by way of example but not limitation, a transistor, an R-S flip-flop, etc.  
         [0020]     In operation, the switching regulator  102  outputs Vout, which is sent as feedback to the error amplifier  104 . The error amplifier output is compared to Vpfm at the PFM comparator  106 . In a non-limiting embodiment, the Vpfm signal has a predetermined valued, but in alternative embodiments, the Vpfm signal may be set dynamically. The output of the PFM comparator  106  is evaluated before turning on the main switch. The results of the comparison are received at the oscillator  108 , and Toff is treated as a control signal that is effective to extend clock off times when error amplifier output is low. Error amplifier output is associated with, for example, a load.  
         [0021]     In operation, the oscillator  108  outputs the clock signal and the ramp signal. The length of clock off times and the length of ramp times depend upon Toff. In a non-limiting embodiment, if the clock off time is to be extended, then the ramp up time is also extended. The PWM comparator  110  compares the level of ramp signal of the oscillator  108  and the output of the error amplifier  104  and provides an input to the latch  112 . The output of the PWM comparator  110  triggers the OFF time of the PWM signal. The other input to the latch  112  is the clock signal, and the latch outputs a PWM signal, which is input to the switching regulator  102 . In a non-limiting embodiment, the clock signal generated by the oscillator  108  triggers the ON time of the PWM signal, which turns on the main switch S 1  after going through a gate driver stage.  
         [0022]     Advantageously, the system  100  enables a system to achieve improved efficiency during light load intervals. This can save power, including increasing battery life in portable electronic devices.  
         [0023]      FIG. 2  depicts an example of various signals that may be generated by the system  100 . Other systems may have similar signal waveforms, or different, depending upon application-specific parameters and aspects. In the example of  FIG. 2 , the signals change from a signal that would correspond to a normal Toff to a Toff that corresponds to a light load. For example, the grid line  202  shows how the signal would continue (in dashed lines) if the Toff did not extend the clock off time. The grid line  204  shows how the signal actually continued in this example, according to a Toff that is associated with a longer clock off time.  
         [0024]     As shown in the example of  FIG. 2 , the output of the error amplifier (EAO) has a ripple waveform, which decreases during the ON time of PWM signal, and increases during the OFF time of the PWM signal. For voltage mode control, at light load where the regulator runs at discontinuous conduction mode (DCM), the EAO level is proportional to the load current. In the example of  FIG. 2 , the comparison of the EAO level with the voltage level Vpfm is examined by a logic circuit within an oscillator, before turning on the main switch. The examination may or may not be triggered by the clock rising edge as shown in the example of  FIG. 2 , or by other timing events such as the zero crossing of inductor current, turning off the main switch, etc. If V(EAO) is larger than Vpfm, the load current is high enough that no PFM is needed, the clock falling edge triggers the PWM signal and a new switching cycle starts.  
         [0025]     In a non-limiting embodiment, when the circuit runs at normal PWM operation, clock signal has a narrow pulse width. As load current decreases, the EAO drops as well. When the examination of comparison of EAO with Vpfm before turning on the main switch finds that V(EAO) is less than Vpfm, the load current is low enough for PFM operation. The clock pulse width is extended and correspondingly the OFF time of the PWM signal is also extended. During this time period, EAO voltage increases. Eventually it will cross the Vpfm threshold. When this happens, the clock signal falls down to trigger the ON time of the PWM signal and a new switching cycle starts. Extended OFF time of PWM signal can be gradually increased from zero to infinite with decreased load current. In this way, it may be possible to achieve close to zero frequency at light load. Light load may correspond to “no load,” but in practical implementations, circuits always have some load.  
         [0026]      FIGS. 3, 4 , and  5  depict alternative examples of systems  300 ,  400 , and  500 , respectively, with a dual mode switching regulator module. The systems  300 ,  400 , and  500  are similar to the system  100 .  
         [0027]     In the example of  FIG. 3 , a switching regulator  302  is depicted in more detail that the switching regulator  102  ( FIG. 1A ). The switching regulator  302  may be implemented in a variety of ways, including by way of example but not limitation, buck, boost, buck-boost, flyback, forward, etc. In the example of  FIG. 3 , a buck regulator is depicted by way of example but not limitation. The switching device S 1  may be implemented as a power MOSFET, rectification device D 1  (may be a rectifier diode, or a synchronous rectifier MOSFET), inductor Lo, input capacitor CIN, and output capacitor Co, form the power stage of the buck regulator, which connects input terminal Vin to a supply source and output terminal Vout to a load.  
         [0028]     An oscillator  308  is similarly depicted in more detail than the oscillator  108  ( FIG. 1B ). In the example of  FIG. 3 , the oscillator  308  includes a current source, timing capacitor, and a hysteresis comparator and a discharging switch. The principles described herein are applicable to any other logic circuit and oscillator topology. The latch  112  ( FIG. 1B ) is depicted as an R-S latch. The operation of the system  300  is similar to that of the system  100 , described previously.  
         [0029]     In the example of  FIG. 4 , a switching regulator  402  is similar to the switching regulator  302  ( FIG. 3 ), but inductor current (IL) may be sampled as labeled. The RC network near the error amplifier  404 , which is similar to the error amplifier  104  ( FIG. 1A ), has a slightly different configuration, but one of skill in the relevant art would understand the significance. The ramp signal and I L  are combined at  414 , and provided as input to the PWM comparator  410 , which is similar to the PWM comparator  110  ( FIG. 1B ).  
         [0030]     The operation of the system  400  is similar to that of the system  100 , but an additional current waveform is added to the ramp signal for easy loop compensation and cycle-by-cycle current limiting. The current could be sensed at the main switch or the inductor or other places and/or means. Due to the simplified loop frequency response, a transconductance amplifier could be used as the error amplifier instead of an operational amplifier. As shown, Ru and Rd form a voltage resistive divider for adjustable output voltage. A series-parallel combination of resistors and capacitors is connected between the output of error amplifier and ground. With peak current mode control, the output of the error amplifier is proportional to the load current over a whole range of load conditions. The operation of the system  400  is similar to that of the system  100 , described previously.  
         [0031]     In the example of  FIG. 5 , a current loop amplifier  516  is added. Instead of using sensed peak current as the control variable, the sensed inductor current goes through the current amplifier  516  to filter out the ripples so the averaged inductor current is used as the control variable. In this way, average current mode control is provided, rather than peak current mode control as in the example of  FIG. 4 .  
         [0032]     It will be appreciated to those skilled in the art that the preceding examples and embodiments are exemplary and not limiting to the scope of the present invention. It is intended that all permutations, enhancements, equivalents, and improvements thereto that are apparent to those skilled in the art upon a reading of the specification and a study of the drawings are included within the true spirit and scope of the present invention. It is therefore intended that the following appended claims include all such modifications, permutations and equivalents as fall within the true spirit and scope of the present invention.