Abstract:
In a telecommunication network where a wireless path is provided between a transmitter and a receiver via a satellite relay forming a multi-hop relayed signal path, a method and system are provided for furnishing adequate signal at a user terminal, which may be in motion, along the propagation path, the method including an open loop component that uses measurements of fading in a received signal at a first terminal to adjust transmit power from the first terminal and further includes a closed loop component that uses measurements of fading in the received signal at a second terminal along with an acknowledgement message and power correction.

Description:
CROSS-REFERENCES TO RELATED APPLICATIONS 
       [0001]    The present application claims benefit under 35 USC §119(e) of U.S. provisional Application No. 60/889,017, filed on Feb. 9, 2007, entitled “Combined Open And Closed Loop Power Control,” the content of which is incorporated herein by reference in its entirety. 
     
    
     STATEMENT AS TO RIGHTS TO INVENTIONS MADE UNDER FEDERALLY SPONSORED RESEARCH OR DEVELOPMENT 
       [0002]    Not Applicable 
       REFERENCE TO A “SEQUENCE LISTING,” A TABLE, OR A COMPUTER PROGRAM LISTING APPENDIX SUBMITTED ON A COMPACT DISK 
       [0003]    Not Applicable 
       BACKGROUND OF THE INVENTION 
       [0004]    This invention relates to wireless communication via a satellite relay and more particularly to regulation of signal power in a wireless network using a satellite relay. 
         [0005]    In a communication environment, power control is a the process by which power level or EIRP of transmissions is adjusted in the presence of varying propagation conditions in order that signals arrive at an intended receiver at a signal level sufficient for accurate reception. Various impediments in a transmission path can cause poor propagation and even loss of signal, including weather, interference, signal reflection, signal blockage, multi-path, and the like. In an environment where a celestial relay station is used, in particular via an orbiting satellite which is subject to severe power budget restrictions, simply adding power is neither possible nor desirable. A source of background information on the problem and a partial proposed solution based on monitoring a beacon reference is described in T. J. Saam, “Uplink Power Control Technique for VSAT Networks,”  IEEE Proceedings -1989  Southeastcon , May 1989, CH-2674-5/89/0000-0096. U.S. Pat. No. 7,110,717 entitled “Leader-Follower Power Control” in the names of two of the present co-inventors and commonly assigned to Viasat of Carlsbad, Calif., provides a further perspective on the problem. Notably, prior approaches did not take into account both short-term and long-term degradation factors along propagation paths. The problem of assuring adequate power to the user terminal at the point of reception is further complicated if the terrestrial terminal is in motion, such as on a motor vehicle or an aircraft. 
         [0006]    What is needed is a power control system and technique to mitigate signal impediments in a wide range of circumstances and thus improve communication reliability without requiring the application of unnecessary power. 
       SUMMARY OF THE INVENTION 
       [0007]    According to the invention, in a telecommunication network where a wireless path is provided between a transmitter and a receiver via a satellite relay forming a multi-hop relayed signal path, a method and system are provided for furnishing adequate signal at a user terminal, which may be in motion, along the propagation path, the method including an open loop component that uses measurements of fading in a received signal at a first terminal to adjust transmit power from the first terminal and further includes a closed loop component that uses measurements of fading in the received signal at a second terminal along with an acknowledgement message and power correction. A speed estimation is employed in the open loop correction control signal path to modulate relatively long-term effects associated with terminal ground speed, along with more rapid closed loop power control. 
         [0008]    The invention will be better understood by reference to the following detailed description in connection with the accompanying documents. 
     
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
         [0009]      FIG. 1  is a block diagram of a system in which the invention is implemented. 
           [0010]      FIG. 2  is a block diagram of a subset of the equipment in user terminal A. 
           [0011]      FIG. 3  is a partial block diagram of a specific embodiment of terminal B. 
           [0012]      FIG. 4  is a graph showing a comparison of probability distribution functions (PDFs) for Monte-Carlo simulation and lognormal approximation. 
           [0013]      FIG. 5  is a graph illustrating open loop power estimate vs. distance of a terminal in motion at 80 km/h 
           [0014]      FIG. 6  is a graph illustrating open loop power estimate vs. C/N 0  showing a decrease in variance with increasing signal to noise ratio. 
           [0015]      FIG. 7  is a graph comparing PDFs for Monte-Carlo simulation (block avg) and lognormal approximation with measured data. 
           [0016]      FIG. 8  is a graph illustrating signal to noise ratio (SNR) Estimation Performance for N=16384. 
           [0017]      FIG. 9  is a graph illustrating amplitude and SINR performance estimates. 
           [0018]      FIG. 10  is a graph illustrating the closed loop power control performance estimates. 
           [0019]      FIG. 11  is a flow diagram of a first embodiment of an open loop process according to the invention. 
           [0020]      FIG. 12  is a flow diagram of a second embodiment of an open loop process according to the invention. 
           [0021]      FIG. 13  is a flow diagram of a third embodiment of an open loop process according to the invention. 
           [0022]      FIG. 14  is a flow diagram of a first embodiment of a combined transmit process according to the invention. 
           [0023]      FIG. 15  is a flow diagram of a second embodiment of a combined transmit process according to the invention. 
           [0024]      FIG. 16  is a flow diagram of a third embodiment of a combined transmit process according to the invention. 
       
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
       [0025]      FIG. 1  illustrates a system  10  in an environment in which the invention is implemented. Two terminals A  12  and B  14 , at least one of which may be in motion from time to time, are coupled in communication via a communication cloud  16  with a relay for example through a communication satellite  18 . The terminals A  12  and B  14  communicate bi-directionally over a bi-directional communication channel of segments  20 ,  22 ,  24 ,  26  as hereinafter explained and that may be subject to degradation, such as short term and long term fading and other propagation effects, including transient interference. The transmission direction from Terminal B to Terminal A is called the forward link (FL) direction and is composed of segments  26  and  22 , and the transmission direction from Terminal A  12  to Terminal B  14  is called the return link (RL) direction and is composed of segments  20  and  24 . More specifically, the forward link (FL) direction comprises an uplink segment (FUL)  26  and a downlink segment (FDL)  22 . The return link (RL) comprises an uplink segment (RUL)  20  and a return downlink segment (RDL)  24 . The purpose of the invention is to control the power level on the return uplink segment (RUL)  20 , particularly where Terminal A  12  is in motion. The forward channel (FL)  22 ,  26  and return channel (RL)  20 ,  24  are not necessarily equivalent in their characteristics, although the long-term characteristics of the two channels are generally correlated, and the short term characteristics are not necessarily correlated. Embedded in each terminal  12  and  14  are an open loop sensor/controller  30 ,  32  and a closed loop controller  34 ,  36 . As hereinafter explained, these controllers may be integrated into a single processor. 
         [0026]      FIG. 2  is a block diagram of a subset of the equipment in user terminal A  12 . The received forward link (FL)  22  signal receives at the terminal  12  a signal on signal line  38 , which is processed for an acknowledgement at an acknowledgement (ACK) detector  40 . The ACK detector  40  operates on decoded data and, upon receipt of an acknowledgement (as herein below explained), supplies a closed loop correction factor C c  via path  42  to a combined open loop/closed loop power control processor  30 ,  34 . If no acknowledgement is received when expected at the acknowledgement detector  40 , this information is passed as a no-acknowledgement received (No ACK REC) signal via path  46  to the combined open loop/closed loop power control processor  30 ,  34  (also called simply the power control processor  35 ). 
         [0027]    The received FL signal  22  is also processed by a forward link metric estimator (FL EST)  48  to create an open loop correction factor C o  in a path  50  to the power control processor  35 . Representative embodiments for the forward link metric are signal power, signal amplitude, and/or signal E b /N 0 . To help explain the subject invention in terms of example embodiments, only signal power and signal to noise ratio E b /N 0  are discussed further below. The representative output of the power control processor  35  is a power control signal  52  applied to a transmitter stage  54 , which in turn serves as a power amplifier for the output of a modulator  55  that itself is fed with user data and the like. The controlled r.f. output of the transmitter stage  54  is supplied to an appropriate antenna  56  that directs its signal on the return uplink  20  to the relay satellite  18  through the communication cloud  16 . 
         [0028]    In one embodiment of the subject invention, and referring to  FIG. 2  and  FIG. 11  showing a first open loop embodiment flow diagram, a representative terminal, e.g., terminal A  12 , is contemplated to be in motion, and the speed of terminal A  12 , as estimated from input from a speed estimator  56  (Step A) is used to calculate the time T to travel the desired distance (Step B) to determine how long the forward link estimator  48  is to observe the received signal before determining the estimated level of the signal and thus to determine the metric to be used for open loop correction. It operates the forward link FL estimate with the parameter T (Step C) and computes the open loop correction Co (Step D) that is then stored for use in the processor  30 ,  34  (Step E). This estimate, which may be a local manual input or an input from a GPS receiver unit, for example, allows the estimator  48  to operate on an “amount-of-distance-traveled” basis, which is useful if terminal A  12  is in motion. 
         [0029]    In another embodiment of the subject invention, and referring to  FIG. 12  showing a second open loop embodiment flow diagram, the estimator  48  retrieves the time T (Step (F) and itself observes the received signal  22  for a specified amount of time before determining the estimated level of the signal (Step G) to determine the metric to be used for the open loop correction (Step H) that is then stored for use in the processor  30 ,  34  (Step E). This allows the estimator  48  to operate on an “amount-of-time-passed” basis, which is useful if terminal B  14  is in motion with its speed unknown at terminal A  12 . 
         [0030]    In yet a third embodiment of the subject invention, and referring to  FIG. 13  showing a third open loop embodiment flow diagram, the speeds of both terminal A  12  and terminal B  14  are measured locally (Step J) and used to determine how long the estimator (e.g.,  48 ) observes the received signal (Step K) before determining the estimated level of the signal (Step L) to determine the metric to be used for open loop correction (Step M) that is then stored for use in the processor  30 ,  34  (Step E). 
         [0031]    According to the invention, the open loop and closed loop corrections C o  and C c , which are related to differing rates of change are used in combination as hereinafter explained to generate the return link transmit power level adjustment  52  that controls the power of the transmitter TX  54  which conveys the modulated data over the communication link RL  20  to the second terminal B  14  ( FIG. 1 ). The combining can be implemented in numerous forms. In one embodiment, and referring to  FIG. 14  showing a flow diagram of first transmit process with a first combining process, the current transmit power is retrieved (Step N) and the total power correction C is computed (Step P) by adding the open loop correction C o  to the closed loop correction C c  The transmit power is then configured (Step Q) and the transmission is effected (Step R). 
         [0032]    In another embodiment and referring to  FIG. 15  showing a second transmit process, the transmission is tested for completeness (Step S) after transmission (Step R as before) and power is updated during transmission (Step T). If transmission is complete, and until receipt is acknowledged (Step U), the open loop correction C o  is added to a set of pre-determined values {Pno_ack} (Step V), which would be used in case an expected ACK is not received (presumably because the previous transmit power level was too low). This operation may occur in both an initial communication phase (such as terminal log-in to a network) or during steady state communication. 
         [0033]    In a third embodiment and referring to  FIG. 16  showing a third transmission process, a combination of the first two embodiments is implemented. For example, a state machine may alternates between ACK and NO-ACK states with appropriate operations in each state, in the NO-ACK state being the correction factor update (Step V previously), and in the ACK state being to update the power correction with the power of the ACK, i.e., Pack (Step W). 
         [0034]      FIG. 3  is a block diagram of a subset  141  of the equipment in user terminal B  14 . Herein, the received Return Link RL  24  signal is the signal to which the power control has been applied. The received RL  24  signal is thus received subject to the degradation of the channel  24 . A return link (RL) estimator  60  at the front end is provided to calculate one or more metrics of the received RL  24  for comparison in an appropriate comparator system  64  with output of an E b /N 0  target  62 . a component that supplies the target value. The error signal on path  67  is supplied through a loop filter  69  as a correction and/or acknowledgement (ACK) on path  71  to a modulator  73  that is configured to use user data and the like to modulate a transmitter TX  75 , which in turn excites the antenna  77  with the forward link signal FL. 
         [0035]    Some example embodiments of a return link metric are the signal amplitude E b  and the signal-to-noise ratio E b /N 0 . For a signal amplitude metric, a Leader-Follower Power Control technique, such as that disclosed in U.S. Pat. No. 7,110,717, may be used. This technique requires a “Leader” terminal, which may be undesirable in some situations (because costs to configure and maintain the leader terminal are required, thereby reducing system capacity and imposing other overhead burdens). 
         [0036]    For a return link signal E b /N 0  metric, the challenge is to estimate noise N 0 . In a multiple access environment, prior techniques used to estimate E b /N 0  first measure E b /(N 0 +I 0 ) and then attempt to remove the I 0  term. This can be computationally difficult and may be prone to excessive and unacceptable estimation error. However, in an embodiment of the present invention, the E b /N 0  metric on return link signal is performed by introducing periodic return link transmission outages during which no terminals are transmitting on the return link  24 . (For example, if the return link  24  is shared by other terminals, then they would all temporarily cease transmission.) The N 0  estimator portion of the return Link estimator  60  monitors the return link  24  channel in these dwell times. Because the N 0  parameter generally varies very slowly (typically primarily due to the diurnal effect of the system heating in the day and cooling at night), the transmission outages would be very short (for example 1 second per hour). During the non-outage periods, the terminals&#39;  12 ,  14 , etc. transmit signal of amplitude E b  would be estimated. The E b /N 0  target  62  is then a fixed constant (dependent on per terminal QoS, for example) and since absolute E b /N 0  estimates are obtained, a leader terminal is not required. 
         [0037]    Implementation Example In order to place the subject invention into a context so that it can be appreciated, an example is presented. In the example, the following assumptions are made:
       1. Hub/Spoke system (Terminal B  14  is a hub, multiple terminals A  12  are the spokes).   2. Return link modulation is spread GMSK.   3. Forward link modulation is QPSK with symbol rate 166 ksps.   4. The channels are a land mobile S-band satellite channel with fixed terminals, land mobile terminals and helicopter terminals.   5. The Return link experiences a relatively high frame error rate (up to 25%).       
 
         [0043]    The power control algorithm according to the invention includes an open loop component and a closed loop component. The open loop component uses measurements of the forward link channel power measured by the terminal to offset the terminal transmit power. The closed loop component uses measurements of the return E b /N 0  and a link-layer acknowledgement and power correction protocol. 
         [0044]    The return channel characteristics depend on the terminal platform dynamics. Three channel models are considered:
       Static Terminal—AWGN channel   Land Mobile Terminal—Rician channel with lognormal shadowing   Helicopter Terminal—Essentially a Rician channel with periodic blockage/distortion due to rotor blades       
 
         [0048]    The Land Mobile link budget assumptions for total error in the power correction algorithm due to the open loop and closed loop is lognormal distributed with zero mean and 1 dB standard deviation. For the static terminal, this assumption is relaxed to 0.5 dB standard deviation. 
         [0049]    Open Loop Power Control: The following describes an open loop power control technique for the invention embodied in a Land Mobile Terminal This technique can be readily programmed to yield the desired outcomes. 
         [0050]    The k th  complex baseband sample of the received forward link sampled signal r f  is modeled as: 
         [0000]        r   f   [k]=α   f   [k]A   f   x   f   [k]+n   c   [k]+jn   s   [k]   (1) 
         [0000]    where α f  is a channel fading coefficient (Rician fast fading random process and Lognormal slow fading random process), A f  is the nominal forward link receive signal amplitude, x f  is the complex baseband modulated signal, and n c  and n s  are the in-phase (cosine) and quadrature (sine) components of the AWGN (zero mean, variance σ 2 ). 
         [0051]    The k th  complex baseband sample of the received return link sampled signal r r  is modeled as 
         [0000]        r   r   [k]=α   r   [k]A   r   x   r   [k]+n   c   [k]+jn   s   [k]+MAI   (2) 
         [0000]    where α r  is a channel fading coefficient (Rician fast fading random process and Lognormal slow fading random process), A r  is the nominal return link receive signal amplitude, x r  is the complex baseband modulated signal, and n c  and n s  are the in-phase (cosine) and quadrature (sine) components of the AWGN (zero mean, variance σ 2 ). 
         [0052]    The return link open loop amplitude fade estimate, {circumflex over (Δ)}, is an estimate obtained from monitoring the forward link. The return link open power control correction, C o , is obtained as 
         [0000]    
       
         
           
             
               
                 
                   
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         [0053]    The following assumptions are made:
       α f  and α f  are independent in the fast fading (Rician) sense but highly correlated in the slow fading (Lognormal) sense. E└|α f   2 |┘=E└|α r   2 |┘≡E[|α 2 |].   The modulated waveforms x f  and x r  are constant envelope   The de-correlation time of the slow fading is greater than the time it takes the terminal to travel ˜2 meters. E└|α 2 |┘≡Δ 2 .       
 
         [0057]    (Measurements of the land mobile satellite channel at S band have confirmed these assumptions. See for instance—Fontan &amp; Vazquez, “S-Band LMS propagation channel behaviour for different environments, degrees of shadowing and elevation angles”,  IEEE Transactions on Broadcasting , March 1998.) 
         [0058]    Based on these assumptions, the terminal can examine the average power over a distance traveled of approximately 2 meters and pre-correct for the lognormal error. The pre-corrected signal received by the hub will experience Rician fading, as well as whatever error is present in the pre-correction process. This error is assumed to be log-normally distributed. It is desired to determine the mean and variance of the estimation error. 
         [0059]    The received power on the forward link, P, is defined as 
         [0000]        P[k]=|r   f   2   [k]|   (3) 
         [0060]    P is used to evaluate {circumflex over (Δ)}, so determine the mean and variance of P. However, this approach has bias problems. It would be better to directly estimate the amplitude or E b /N 0 . 
         [0061]    Analysis of a single sample: An analysis of a sample is useful to an understanding of the invention. First, determine the mean and variance of the estimator using only a single sample of P. 
         [0000]        E[P[k]]=E[|r   f   2   [k]|]=E └|(α f   [k]A   f   x   f   [k]+n   c   [k]+jn   s   [k] ) 2 |┘.  (4) 
         [0062]    Simplifying notation results only in 
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         [0064]    The x 2  term has vanished due to the assumption that a constant envelope exists. Reorganizing terms results in: 
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         [0065]    Comparing this estimate to the nominal transmission (considered the last transmission with a closed loop update), one can determine {circumflex over (Δ)}. 
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         [0066]    The estimate {circumflex over (Δ)} is biased, but the bias is small for high signal-to-noise ratio. 
         [0067]    The 2 nd  moment of P is (with some interim calculation steps omitted): 
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                   ( 
                   12 
                   ) 
                 
               
             
           
         
       
     
         [0068]    where K is the Rician K factor. 
         [0069]    The variance of P is then 
         [0000]    
       
         
           
             
               
                 
                   
                     var 
                      
                     
                       [ 
                       
                         P 
                          
                         
                           [ 
                           k 
                           ] 
                         
                       
                       ] 
                     
                   
                   = 
                   
                     
                       E 
                        
                       
                         [ 
                         
                           
                             P 
                              
                             
                               [ 
                               k 
                               ] 
                             
                           
                            
                           
                             
                               P 
                               * 
                             
                              
                             
                               [ 
                               k 
                               ] 
                             
                           
                         
                         ] 
                       
                     
                     - 
                     
                       
                         
                           E 
                            
                           
                             [ 
                             
                               P 
                                
                               
                                 [ 
                                 k 
                                 ] 
                               
                             
                             ] 
                           
                         
                         2 
                       
                       . 
                     
                   
                 
               
               
                 
                   ( 
                   13 
                   ) 
                 
               
             
             
               
                 
                   = 
                   
                     
                       
                         A 
                         2 
                       
                        
                       
                         
                           
                             8 
                             + 
                             
                               16 
                                
                               K 
                             
                             + 
                             
                               4 
                                
                               
                                 K 
                                 2 
                               
                             
                           
                           
                             
                               ( 
                               
                                 
                                   2 
                                    
                                   K 
                                 
                                 + 
                                 1 
                               
                               ) 
                             
                             2 
                           
                         
                       
                     
                     + 
                     
                       8 
                        
                       
                         A 
                         2 
                       
                        
                       
                         Δ 
                         2 
                       
                        
                       
                         σ 
                         2 
                       
                     
                     + 
                     
                       8 
                        
                       
                         σ 
                         4 
                       
                     
                     - 
                     
                       
                         
                           ( 
                           
                             
                               
                                 Δ 
                                 2 
                               
                                
                               
                                 A 
                                 2 
                               
                             
                             + 
                             
                               2 
                                
                               
                                 σ 
                                 2 
                               
                             
                           
                           ) 
                         
                         2 
                       
                       . 
                     
                   
                 
               
               
                 
                   ( 
                   14 
                   ) 
                 
               
             
             
               
                 
                   = 
                   
                     
                       
                         A 
                         4 
                       
                        
                       
                         
                           
                             8 
                             + 
                             
                               16 
                                
                               K 
                             
                             + 
                             
                               4 
                                
                               
                                 K 
                                 2 
                               
                             
                           
                           
                             
                               ( 
                               
                                 
                                   2 
                                    
                                   K 
                                 
                                 + 
                                 1 
                               
                               ) 
                             
                             2 
                           
                         
                       
                     
                     + 
                     
                       4 
                        
                       
                         A 
                         2 
                       
                        
                       
                         Δ 
                         2 
                       
                        
                       
                         σ 
                         2 
                       
                     
                     + 
                     
                       4 
                        
                       
                         σ 
                         4 
                       
                     
                     - 
                     
                       
                         A 
                         4 
                       
                        
                       
                         
                           Δ 
                           2 
                         
                         . 
                       
                     
                   
                 
               
               
                 
                   ( 
                   15 
                   ) 
                 
               
             
           
         
       
     
         [0070]    Monte-Carlo simulation (“measured data  80 ”) generally agrees with the analytic results  82  above and confirms that the open loop error is roughly log normally distributed, as shown in  FIG. 4 , which is a graph showing a comparison of probability distribution functions (PDFs) for Monte-Carlo simulation as measured data  80  and the corresponding lognormal approximation  82 , where the Rician K=15 dB, C/N 0 =58 dB, and the sample rate is 166 kHz). 
         [0071]    Analysis of a block of samples: The variance between the measured data and the analytic result can be reduced by averaging over a block of N samples. 
         [0000]    
       
         
           
             
               
                 
                   
                     P 
                     avg 
                   
                   = 
                   
                     
                       1 
                       N 
                     
                      
                     
                       
                         ∑ 
                         
                           k 
                           = 
                           
                             k 
                             0 
                           
                         
                         
                           
                             k 
                             0 
                           
                           + 
                           N 
                           - 
                           1 
                         
                       
                        
                       
                         P 
                          
                         
                           [ 
                           k 
                           ] 
                         
                       
                     
                   
                 
               
               
                 
                   ( 
                   16 
                   ) 
                 
               
             
           
         
       
     
         [0072]    For a sample rate of 166 kHz and a terminal velocity of 80 km/h, N=16384 is about 2.1 m. The reduction in variance is shown in  FIG. 5  for three different C/N 0  values: 48, dB ( 84 ), 58 dB ( 86 ) and 68 dB ( 88 ). 
         [0073]    The statistics are heavily affected by the C/N 0 , as shown in  FIG. 6 , which shows the mean  90  and variance  92  of the open loop power estimate in dB vs. C/N 0  in dB with block averaging statistics for N=16384. While the variance decreases with decreasing C/N 0  (a surprising result), the overall error (including mean error) increases as expected with decreasing C/N 0 . Exact analytic expressions for the mean and variance of average power P avg  have not been determined. Approximations based on statistics are suitable. 
         [0074]    A look at the PDF of the block averaged Monte Carlo simulation power errors ( FIG. 7 ) again shows a lognormal distribution is an appropriate choice. Note how closely the lognormal theoretical curve  94  approximation matches the measured data  96  of a Monte Carlo simulation. 
         [0075]    SNR Estimation: There is a large bias associated with power estimation at the expected C/N 0  operating range. Instead of estimating change in received power, an estimated change in received SNR can be used. In this case, the return link open loop amplitude fade estimate, {circumflex over (Δ)}, is given by 
         [0000]    
       
         
           
             
               
                 
                   
                     Δ 
                     ^ 
                   
                   = 
                   
                     
                       
                         SNR 
                         estimate 
                       
                       
                         SNR 
                         nominal 
                       
                     
                   
                 
               
               
                 
                   ( 
                   
                     16 
                      
                     b 
                   
                   ) 
                 
               
             
           
         
       
     
         [0000]    where SNR estimate  is the estimate of the SNR, and SNR nominal  is the nominal SNR corresponding to α=1. 
         [0076]    There are a variety of data-aided (DA) and non-data-aided (NDA) techniques available for performing SNR estimation. Non-data-aided techniques are desirable, because they do not require phase tracking in the fast fading Rician environment. Two such NDA techniques have been investigated in Rician fading. These estimates are derived based on higher order statistics of a Gaussian random variable, but they appear to work effectively for a Rician channel as well. 
         [0077]    The M2M4 estimator is: 
         [0000]    
       
         
           
             
               
                 
                   
                     M 
                     2 
                   
                   = 
                   
                     E 
                      
                     
                       ⌊ 
                       
                         
                           r 
                            
                           
                             [ 
                             k 
                             ] 
                           
                         
                          
                         
                           
                             r 
                              
                             
                               [ 
                               k 
                               ] 
                             
                           
                           * 
                         
                       
                       ⌋ 
                     
                   
                 
               
               
                 
                   ( 
                   17 
                   ) 
                 
               
             
             
               
                 
                   
                     M 
                     4 
                   
                   = 
                   
                     E 
                      
                     
                       ⌊ 
                       
                         
                           ( 
                           
                             
                               r 
                                
                               
                                 [ 
                                 k 
                                 ] 
                               
                             
                              
                             
                               
                                 r 
                                  
                                 
                                   [ 
                                   k 
                                   ] 
                                 
                               
                               * 
                             
                           
                           ) 
                         
                         2 
                       
                       ⌋ 
                     
                   
                 
               
               
                 
                   ( 
                   18 
                   ) 
                 
               
             
             
               
                 
                   
                     SNR 
                     
                       
                         M 
                         2 
                       
                        
                       
                         M 
                         4 
                       
                     
                   
                   = 
                   
                     
                       
                         
                           2 
                            
                           
                             M 
                             2 
                             2 
                           
                         
                         - 
                         
                           M 
                           4 
                         
                       
                     
                     
                       
                         M 
                         2 
                       
                       - 
                       
                         
                           
                             2 
                              
                             
                               M 
                               2 
                               2 
                             
                           
                           - 
                           
                             M 
                             4 
                           
                         
                       
                     
                   
                 
               
               
                 
                   ( 
                   19 
                   ) 
                 
               
             
           
         
       
     
         [0078]    The SVR estimator is: 
         [0000]    
       
         
           
             
               
                 
                   β 
                   = 
                   
                     
                       E 
                        
                       
                         [ 
                         
                           
                             r 
                              
                             
                               [ 
                               k 
                               ] 
                             
                           
                            
                           
                             
                               r 
                                
                               
                                 [ 
                                 k 
                                 ] 
                               
                             
                             * 
                           
                            
                           
                             r 
                              
                             
                               [ 
                               
                                 k 
                                 - 
                                 1 
                               
                               ] 
                             
                           
                            
                           
                             
                               r 
                                
                               
                                 [ 
                                 
                                   k 
                                   - 
                                   1 
                                 
                                 ] 
                               
                             
                             * 
                           
                         
                         ] 
                       
                     
                     
                       
                         E 
                          
                         
                           [ 
                           
                             
                               ( 
                               
                                 
                                   r 
                                    
                                   
                                     [ 
                                     k 
                                     ] 
                                   
                                 
                                  
                                 
                                   
                                     r 
                                      
                                     
                                       [ 
                                       k 
                                       ] 
                                     
                                   
                                   * 
                                 
                               
                               ) 
                             
                             2 
                           
                           ] 
                         
                       
                       - 
                       
                         E 
                          
                         
                           [ 
                           
                             
                               r 
                                
                               
                                 [ 
                                 k 
                                 ] 
                               
                             
                              
                             
                               
                                 r 
                                  
                                 
                                   [ 
                                   k 
                                   ] 
                                 
                               
                               * 
                             
                              
                             
                               r 
                                
                               
                                 [ 
                                 
                                   k 
                                   - 
                                   1 
                                 
                                 ] 
                               
                             
                              
                             
                               
                                 r 
                                  
                                 
                                   [ 
                                   
                                     k 
                                     - 
                                     1 
                                   
                                   ] 
                                 
                               
                               * 
                             
                           
                           ] 
                         
                       
                     
                   
                 
               
               
                 
                   ( 
                   20 
                   ) 
                 
               
             
             
               
                 
                   
                     SNR 
                     SVR 
                   
                   = 
                   
                     β 
                     - 
                     1 
                     + 
                     
                       
                         β 
                          
                         
                           ( 
                           
                             β 
                             - 
                             1 
                           
                           ) 
                         
                       
                     
                   
                 
               
               
                 
                   ( 
                   21 
                   ) 
                 
               
             
           
         
       
     
         [0079]    In implementation, the expectations in the above equations are based on time series averages. For this simulation, the time series averages were performed over 16384 symbols (roughly the time it takes the terminal to move 2.1 m at 80 km/hr). 
         [0080]      FIG. 8  shows the performance for the M2M4 and SVR SNR estimates for a Rician K=15 dB channel over a +/−10 dB range of average C/N 0  operating points. The SVR technique represented by curve  102  performs significantly better than the M2M4 technique represented by curve  106  at moderate and high average SNR, while also experiencing very small bias (curve  104 ) over the entire range as compared to M2M4 bias (curve  108 ). 
         [0081]    Closed Loop Power Control: The closed loop portion  34  ( FIG. 1 ) of the power controller  35  is embodied in a technique that is based on measurements of the terminal&#39;s received de-spread amplitude in comparison to that of a “leader” terminal (not shown). 
         [0082]    A link-level acknowledgement protocol is used on the forward link  22 . If a return link burst is received by the hub (not shown) of the system and decoded error free, an acknowledgement (ACK) is transmitted to the terminal  12 . The acknowledgement contains a power correction. Because the target frame error rate (at system capacity in the Rician channel) is ˜25%, there is a mild inherent negative bias in the power control algorithm. Therefore, if the terminal does not receive an acknowledgement it automatically applies a positive power correction, as in  FIGS. 15 and 16 . 
         [0083]    A Monte Carlo simulation has been used to determine if the closed loop power control error is roughly lognormal, what the power control statistics are, and what the appropriate no-acknowledge power correction should be. The Monte Carlo simulation description is as follows:
       1. The terminal transmits a burst with per bit energy E b . The simulation is initialized with E b  equal to the E b,target  (the terminal has just logged in).   2. The burst amplitude is attenuated by a Rician fading coefficient α. (This assumes that fade is constant over the duration of the terminal&#39;s burst. For high velocity terminals, this assumption does not hold and thus results are inaccurate and pessimistic.)   3. Multiple access interference is modeled by an measuring the power of other transmitting terminals that overlap this terminal&#39;s burst. The other terminals have an exponential arrival time, and N of them have some fraction of their burst overlap the burst of interest. The k th  terminal overlaps the burst of interest by fraction τ k , transmits E b, target  per bit energy with a 1 dB standard deviation lognormal power error p k , and has its burst amplitude attenuated by a Rician fading coefficient α k . There are K symbols per information bit, and the spreading efficiency of the GMSK waveform is β. The SINR is given by:       
 
         [0000]    
       
         
           
             
               
                 
                   
                     
                       E 
                       b 
                     
                     
                       
                         N 
                         0 
                       
                       + 
                       
                         I 
                         0 
                       
                     
                   
                   = 
                   
                     
                       
                         α 
                         2 
                       
                        
                       
                         E 
                         b 
                       
                     
                     
                       
                         N 
                         0 
                       
                       + 
                       
                         
                           1 
                           
                             β 
                              
                             
                                 
                             
                              
                             
                               K 
                               spread 
                             
                           
                         
                          
                         
                           
                             ∑ 
                             
                               k 
                               = 
                               1 
                             
                             N 
                           
                            
                           
                             
                               α 
                               k 
                               2 
                             
                              
                             
                               p 
                               k 
                             
                              
                             
                               τ 
                               k 
                             
                              
                             
                               E 
                               
                                 b 
                                 , 
                                 target 
                               
                             
                           
                         
                       
                     
                   
                 
               
               
                 
                   ( 
                   22 
                   ) 
                 
               
             
           
         
       
       
         
           
             4. The probability that the burst of interest is successfully decoded by the hub is based on an 848-bit block FER curve. The decode probability threshold is based on the SINR. A uniform random number is chosen, and if it exceeds the threshold the burst is successfully decoded. 
             5. The terminal&#39;s transmit amplitude (including Rician fading coefficient) is estimated. There is a lognormal distribution to the amplitude estimation error, shown by the curves  110 ,  112 ,  114 ,  116  for no fading, and K=14.8, 10.2 and 7.0, respectively, in  FIG. 9 . The SINR (not SNR) is used to pick the appropriate sigma. The amplitude estimation error is ε. 
             6. The power correction (for successful decoding) in dB is determined by 
           
         
       
     
         [0000]        C   c,dB   =PC   ack =0.25[log 10 ( E   b,target )−10 log 10 (α 2   E   b ε)]  (23)       7. The power correction at the terminal is applied by         
         [0000]      E b ←E b 10 log 10 [(1−ack)PC noack +ack·PC ack ]  (24) 
         [0091]    The closed loop power control performance, that is Eb bias  118  and variance  120 , is shown in  FIG. 10 . The performance is shown for Rician K=15 dB, average terminal arrival rate 25.6/burst time, acknowledgement loop gain of 0.25 dB, lognormal power control error=1 dB sigma, target Eb/N 0  of 9.6 dB, and spread factor  66  with GMSK BT=0.5. These studies demonstrate that a combined open-loop/closed-loop power control technique is a workable solution in the intended environment. 
         [0092]    The invention has been explained with reference to specific embodiments and examples. Other embodiments will be evident to those of skill in the art. It is therefore not intended that the invention be limited, except as indicated by the appended claims.