Abstract:
A device converting electric power between a voltage source and a current source, comprising several stages ( 8   i ) of switching cells ( 10   i , k ) comprising each two switches ( 12   i , k   , 14   i , k ), capacitors ( 20   i , k ) associated with the cells ( 10   i , k ) arranged in a row ( 18   k ) increasing from current source ( 4 ), control devices ( 16   i , k ) each connected to a cell ( 10   i , k ) and elements for monitoring the control devices ( 16   i , k ) . The stages ( 8   i ) define two end groups and at least an intermediate group of switches, the two end groups comprising switches of each cell belonging respectively to the first and last stage connected in series, the intermediate group comprising pairs of switches ( 12   i , k   , 14   i−1 , k ) of cells belonging to two neighbouring stages connected in series. Furthermore, the capacitors ( 20   i , k   , 20   n , k ) of a common row ( 18   k ) are transversely connected in series between the two end groups.

Description:
FIELD OF THE INVENTION 
   The present invention relates to a device for reversible conversion of electrical energy between a DC voltage source and a current source. 
   BACKGROUND OF THE INVENTION 
   More particularly, the invention relates to such a device comprising, on the one hand, switching cells each having two switches, each switch itself being constituted by at least one component forming a switch, and, on the other hand, capacitors associated with the switching cells and adapted to maintain between the homologous terminals of the two switches of each cell a load voltage equal to a fraction of the voltage of the voltage source, increasing as a function of its rank starting from the current source, and the homologous terminals of the switches situated at the end of the device close to the current source being “short-circuitable”, and furthermore control devices each connected to a switching cell and adapted to control the switchings of the two switches of the cell whilst ensuring opposite states for them, as well as means for operating the control devices adapted to supply a reference signal adapted to the desired conversion. 
   Such a device for reversible conversion of electrical energy is described in the European Patent published under the number EP 0 555 432. 
   It comprises N switching cells, N being any whole number greater than or equal to 2. Each cell is composed of two switches which are controlled to have complementary states at each instant. N switches of the N cells are connected in series and constitute a first series of the device, the N other switches being connected in series and forming a second series of the device. 
   The two series of switches are interconnected, on the one hand, by a common extremity to a current source and, on the other hand, by their opposite extremities to the terminals of a voltage source. 
   A capacitor which is connected between the symmetrical terminals of the two switches of the cell concerned is associated with each switching cell. The cell closest to the voltage source may be associated with a specific capacitor in the hypothetical case in which the voltage source is not an ideal source in order to compensate for these imperfections. 
   In the contrary case, the perfect voltage source plays the role of capacitor with regard to this cell. 
   Each capacitor has as its function to maintain a voltage known as a capacitor load voltage at its terminals. 
   A distribution of these load voltages proportional to the rank k of each capacitor, 
           Vc   k     =     kV   N       ,       
 
V being the voltage at the terminals of the voltage source, assures at the terminals of the blocked switches a voltage difference equal to 
       V   N       
 
for all the blocked switches. Thus each capacitor is chosen so as to present a behaviour under voltage as an increasing function of its rank, greater than the value 
         kV   N     .       
 
   In addition, control logics can be synchronised in such a way that the ripple of the output voltage of the device has an amplitude equal to 
       V   N       
 
and a frequency equal to NF, where F is the switching frequency of the switching cells.
 
   This output voltage is the voltage between the terminal of the voltage source situated at the lowest potential and the terminal of the current source connected to the conversion device. 
   However, we are witnessing nowadays the development of high-powered electrical energy conversion devices for increasingly high voltage levels of the voltage source. This voltage increase leads indirectly to an increase in the size of the capacitors of the device which have to support increasingly substantial fractions of this voltage. Also nowadays, above 6 kV the price and the volume of the device tend to become prohibitive. 
   SUMMARY OF THE INVENTION 
   The invention seeks to remedy these drawbacks of the conventional device described previously by creating a device for reversible conversion of electrical energy which is capable of extending the field of use of high-powered conversion devices towards increasingly high voltage levels whilst permitting a substantial reduction in its volume and retaining the properties of the converter described in the publication EP 0 555 432 which are set out above. 
   Therefore the invention relates to a device for reversible conversion of electrical energy of the aforesaid type, characterised in that it comprises at least two parallel-connected stages each having at least two cells and at least one capacitor, the said stages defining two end groups of switches and at least one intermediate group of switches common to two successive stages, the two end groups each comprising switches of each cell belonging respectively to the first and to the last series-connected stages, the intermediate group comprising pairs of switches of cells belonging to two neighbouring series-connected stages, and that the capacitors are connected transversely in series between the two end groups. 
   The device for reversible conversion of electrical energy according to the invention may also have one or more of the following characteristics: 
   the intermediate group comprises series-connected switches of cells belonging alternately to two neighbouring stages, the said switches being unidirectional in voltage and bidirectional in current; 
   the two switches of each of the said pairs are connected in parallel and are bidirectional in voltage and unidirectional in current; 
   the components forming switches are all identical and each switch is constituted by series-connected components, the number of which is a function of the maximum voltage applicable between its terminals; 
   the operating means include means for processing the reference signal so as to deliver at the output a plurality of secondary reference signals, and means for transmission of each secondary reference signal to all the switching cell control devices of one and the same stage; 
   the processing means are adapted to deliver a plurality of secondary reference signals of which the sum of the values at each instant is proportional to the value of the reference signal, each secondary reference signal of a stage situated, on the voltage source side, between two given potential levels having at each instant a value higher than the value of a secondary reference signal of a stage situated, on the voltage source side, between two higher potential levels; 
   the device has two stages; 
   the part of the device situated between the two capacitors closest to the current source and the current source itself includes two components forming series-connected switches on each of the first and last groups and two diodes connected, on the one hand, at a point situated between the said two capacitors and, on the other hand, at a point situated between the said two components of the first and last groups respectively; 
   each stage includes two switching cells; and 
   each stage includes three switching cells. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
     The invention will be better understood with the aid of the following description which is given by way of example with reference to the accompanying drawings, in which: 
       FIG. 1  shows an electrical block diagram of a conversion device according to the invention in the more general case, in which the control unit is not shown; 
       FIG. 2  shows an electrical block diagram of a conversion device according to the invention in the case where it has two stages and two cells per stage, also detailing a control unit for this device; 
       FIG. 3  shows an electrical diagram detailing an embodiment of the switching cells of the conversion device shown in  FIG. 2 ; 
       FIG. 4  shows the behaviour of the reference signals of a control unit of the conversion device shown in  FIG. 2 ; 
       FIG. 5  shows the behaviour of the input and output signals of a first control device of the conversion device shown in  FIG. 2 ; 
       FIG. 6  shows the behaviour of the input and output signals of a second control device of the conversion device shown in  FIG. 2 ; 
       FIG. 7  shows the behaviour of the input and output signals of a third control device of the conversion device shown in FIG.  2 : 
       FIG. 8  shows the behaviour of the input and output signals of a fourth control device of the conversion device shown in  FIG. 2 ; 
       FIG. 9  shows the behaviour of the currents circulating through two capacitors of the first and second stages respectively, of the conversion device shown in  FIG. 2 ; 
       FIG. 10  shows the behaviour of the standardised output voltage of the conversion device shown in  FIG. 2 ; and 
       FIG. 11  shows an electrical diagram of a conversion device with two stages and two cells per stage, according to another possible embodiment of the invention. 
   

   DETAILED DESCRIPTION OF THE INVENTION 
   The device for reversible conversion of electrical energy which is shown in  FIG. 1  has a DC voltage source  2  ensuring a potential difference of value E between its terminals and a current source  4  delivering a direct or alternating current I according to the application envisaged. 
   Thus, for example, when the current source delivers a symmetrical alternating current the conversion device corresponds to a voltage inverter or, taking account of the reversibility, to a current rectifier. The following description always assumes this particular case. 
   The voltage source consists of n secondary voltage sources  6   1 , . . . ,  6   n  connected in series and each defining between its terminals n successive stages  8   1 , . . . ,  8   n . Any secondary source  6   i  is for example constituted by a capacitor and maintains a partial voltage 
       E   n       
 
between its terminals. In the following, the stages are numbered in the increasing order of the potential levels to which they are connected on the voltage source side.
 
   Each stage  8   i  has p switching cells  10   i1 , . . . ,  10   ip . Each switching cell  10   il  is constituted by two switches  12   ik  and  14   ik  kept in opposite states by a device  16   ik  for controlling the switching thereof connected to the cell  10   ik . The control devices form part of a control unit which will be described in detail during the description of FIG.  2 . 
   Thus the n stages define n+1 groups of switches, each of the said groups being connected by one end to the current source and by the other end to one of the n+1 potential levels of the series of secondary voltage sources  6   1 , . . . ,  6   n . As for the stages, the groups of switches are numbered in the increasing order of the potential levels to which they are connected on the side of the secondary voltage sources. Thus the first group is connected to the terminal of the voltage source  2  with the lowest potential and the last group is connected to the terminal of the voltage source  2  with the highest potential. 
   The first group of switches is constituted by the switches  12   1,1 , . . . ,  12   1,p  of the switching cells of the first stage, connected in series. The (n+1)-th group of switches is constituted by the switches  14   n,1 , . . . ,  14   n,p  of the p switching cells of the n-th stage, connected in series. The i-th group of switches, with  1 &lt;i[n, is constituted by the switches  12   i,1 , . . . ,  12   i,p  of the p switching cells of the i-th stage and the switches  14   i−1,1 , . . . ,  14   i−1,p  of the p switching cells of the (i−1)-th stage, connected alternately in series. 
   In this way, p ranks  18   1 , . . . ,  18   p  are defined transversely with respect to the n stages, each rank  18   k  having n switching cells, that is to say  10   1,k , . . . ,  10   n,k . 
   Between two successive ranks  18   k  and  18   k+1 , n capacitors of rank k,  10   1,k , . . . ,  20   n,k , are connected in series at the rate of one per stage. Thus at the i-th stage the capacitor  20   i,k  is connected, on the one hand, to the i-th group of switches and, on the other hand, to the (i+1)th group of switches. Moreover, each capacitor is adapted to maintain between its terminals a load voltage increasing as a function of its rank k and representing a fraction of the partial voltage of the secondary voltage source of the stage to which it belongs. For example, a distribution of these load voltages which is proportional to the rank of each capacitor  20   i,k , 
           E     i   ,   k       =     kE   pn       ,       
 
guarantees at the terminals of the open switches a voltage difference less than or equal to 
         E   pn     .       
 
   The conversion device shown in  FIG. 2  is a particular case of the device described previously, in an embodiment of the invention adapted for use with a DC voltage source and an alternating current source of frequency f i . It has two stages  8   1  and  8   2  and two ranks  18   1  and  18   2 . 
   E is the voltage of the DC voltage source  2  which loads two capacitors  6   1  and  6   2  each constituting a secondary voltage source for each stage, with partial voltage 
         E   2     .       
 
Between the two ranks  18   1  and  18   2  two capacitors  20   1,1  and  20   2,1  are connected in series as described previously and are dimensioned so as to support a load voltage as a function of their rank (k=1), with a value of 
         E     1   ,   1       =       E   2.1     =       E   4     .           
 
   The device also has four switching cells  10   1,1 ,  10   1,2 ,  10   2,1 ,  10   2,2  controlled respectively by four control devices  16   1,1 ,  16   1,2 ,  16   2,1 ,  16   2,2 . These four control devices are synchronised and deliver logic control signals at a frequency F which are adapted to ensure the switching to opposite states of the two switches of each cell. 
   In the embodiment described here, the frequency F is clearly higher than the frequency f i  and is chosen to represent more precisely a multiple of f i  for the sake of simplicity. 
   Each control device has for example a comparator of which the logic state at the output is the result of the comparison of two signals of which one comes from a synchronisation module  22  and the other comes from an operating generator  24 . 
   Therefore the control device  16   i,k  supplies at the output a control signal sc i,k  of which the value determines the state of the switching cell  10   i,k . Thus, for example, when the control signal sc i,k  is equal to 1, the switch  12   i,k  of the switching cell  10   i,k  is blocked and the switch  14   i,k  of this same cell is passing. Conversely, when the control signal sc i,k  is equal to 0, the switch  12   i,k  of the switching cell  10   i,k  is passing and the switch  14   i,k  of this same cell is blocked. The simultaneous control of the two switches of one and the same cell to opposing states will not be described in greater detail here as it is considered as known in the prior art. 
   The synchronisation module  22  comprises means  26  for generating symmetrical alternating triangular signals of frequency F as well as a delay circuit  28  which generate two signals sd 1  and sd 2  offset by a time difference equal to 
       1     2   ⁢   F         
 
and supplying respectively the first rank control devices  16   1,1 ,  16   2,1  and the second rank control devices  16   1,2 ,  16   2,2 .
 
   The operating generator  24  for its part delivers a symmetrical alternating reference signal sr of frequency f i  identical to the frequency of the current source  4 . 
   This reference signal is processed at the output of the operating generator  24  by two processing modules respectively  30  and  32  of the first and second stage, in order to supply respectively at the output two secondary reference signals sr 1  and sr 2 . These two signals sr 1  and sr 2  supply respectively the first stage control devices  16   1,1 ,  16   2,1  and the second stage control devices  16   1,2 ,  16   2,2 . 
   For good operation of the conversion device, the signals sr 1  and sr 2  verify the following two relationships:
 
 sr   1   +sr   2 =2 sr, sr   1   sr   2 .
 
   The two processing modules  30 and  32  which permit the supply of such signals from the reference signal sr are considered as conventional and therefore will not be described in detail below. 
   As shown in  FIG. 3 , the switches of the converter are all of the same type, that is to say bidirectional in current and unidirectional in voltage and are formed by IGBT transistors each associated with a diode in antiparallel. Depending upon the applications, each of these IGBT transistors can be replaced by a bipolar Darlington, MOST, GTO, etc. transistor. 
   In this embodiment it will be noted that the four switches of the first and last groups are capable of supporting a voltage double that supported by the four switches of the second group. This poses a problem of heterogeneous dimensioning of the switches of the conversion device. In order to solve this problem, it is preferable to replace each of the four switches of the first and last groups by two identical switches connected in series and positioned in the same state at each instant, which does not in any way modify the operation of the device. 
     FIG. 4  shows the behaviour of the reference signal sr and of the secondary reference signals sr 1  and sr 2  in the chosen embodiment, that is to say for a DC voltage source and an alternating current source of frequency f i . 
   The signal sr is here represented without unit, as the sum of a continuous signal with a value 0.5 and a sinusoidal signal with an amplitude substantially lower than 0.5 and with a frequency f 1  normalised at 1. The signal sr 1  is then defined by the following relationship: 
       {               sr   1     =     2   ×   sr       ,           if   ⁢           ⁢     sr   [   0.5                     sr   1     =   1     ,           if   ⁢           ⁢   sr   ⁢           ⁢   ℳ   ⁢           ⁢   0.5                   
 
   The signal sr 2  for its part is defined by the relationship: 
       {               sr   2     =   0     ,           if   ⁢           ⁢     sr   [   0.5                     sr   2     =       2   ×   sr     -   1       ,             if   ⁢           ⁢   sr   ⁢           ⁢   ℳ   ⁢           ⁢   0.5     ⁢                           
 
   It is easily verified that thus, at any instant, the two conditions sr 1 +sr 2 =2sr and sr 1             sr 2  are verified.
     FIG. 5  shows, on the one hand, the behaviour of the two signals sr 1  and sd 1  supplied at the input of the control device  16   1,1  and, on the other hand, the behaviour of the control signal sc 1,1  supplied at the output of the same control device  16   1,1 , as a function of the signals supplied at the input. 
   The signal sd 1  is a triangular signal with an amplitude varying between 0 and 1 and a frequency F which here has the value  20   f   i . The resulting signal sc 1,1  is a square wave signal of zero value when the relationship sd 1 &gt;sr 1  is verified and of unit value when the relationship sd 1 &lt;sr 1  is verified. 
     FIG. 6  shows, on the one hand, the behaviour of the two signals sr 1  and sd 2  supplied at the input of the control device  16   1,2  and, on the other hand, the behaviour of the control signal sc 1,2  supplied at the output of the same control device  16   1,2 , as a function of the signals supplied at the input. 
   The signal sd 2  is a triangular signal with an amplitude varying between 0 and 1 and a frequency F, offset by a time difference equal to 
       1     2   ⁢   F         
 
relative to the signal sd 1 . The signal sc 1,2  is then a square wave signal of zero value when the relationship sd 2 &gt;sr 1  is verified and of unit value when the relationship sd 2 &lt;sr 1  is verified.
 
     FIG. 7  shows, on the one hand, the behaviour of the two signals sr 2  and sd 1  supplied at the input of the control device  16   2,1  and, on the other hand, the behaviour of the control signal sc 2,1  supplied at the output of the same control device  16   2,1 , as a function of the signals supplied at the input. 
   The signal sc 1,1  is then a square wave signal of zero value when the relationship sd 1 &gt;sr 2  is verified and of unit value when the relationship sd 1 &lt;sr 2  is verified. 
     FIG. 8  shows, on the one hand, the behaviour of the two signals sr 2  and sd 2  supplied at the input of the control device  16   2,2  and, on the other hand, the behaviour of the control signal sc 2,2  supplied at the output of the same control device  16   2,2 , as a function of the signals supplied at the input. 
   The signal sc 2,2  is then a square wave signal of zero value when the relationship sd 2 &gt;sr 2  is verified and of unit value when the relationship sd 2 &lt;sr 2  is verified. 
     FIG. 9  shows the behaviour of the currents i 1,1  and i 2,1  which pass respectively through the two capacitors  20   1,1  and  20   2,1 . 
   The value of these currents is directly linked to the synchronisation of the control devices, as described previously, and thus is controlled so as to have an average zero value over a period 
       1   F       
 
in such a way as to ensure a constant average voltage of 
       E   4       
 
at the terminals of the capacitors  20   1,1  and  20   2,1 .
 
     FIG. 10  shows the behaviour of the standardised output voltage Vs of the conversion device. This is measured between the lowest potential level of the voltage source  2  and the terminal of the current source  4  connected to the energy conversion device. 
   The output voltage has a ripple of frequency 2F and of amplitude 
         E   4     ;       
 
these two conditions facilitate the filtering of this voltage.
 
   An energy conversion device with two ranks and two stages according to another possible embodiment of the invention is shown in FIG.  11 . 
   The switches of the first and third groups each have two components forming switches. By contrast, the intermediate group of switches only appears in the second rank. In the first rank  18   1  a first diode  34  is connected, on the one hand, to a point situated between the two components  38  and  40  of the first group and of the first rank and, on the other hand, to a point situated between the two capacitors  20   1,1  and  20   2,1 . 
   Likewise a second diode  36  is connected, on the one hand, to a point situated between the two capacitors  20   1,1  and, on the other hand, to a point situated between the two components  42  and  44  of the third group and of the first rank. 
   This embodiment includes a control unit which is substantially different from the control unit described previously in so far as the control of the first rank  18   1  is concerned. However, this new control unit can be deduced in a conventional manner from the one previously described in  FIG. 2  with the aid of a simple combination of the control devices  16   1,1  and  16   2,1  of the switching cells of the first rank  18   1 . 
   For good operation of the device, the component  38  situated on the first group, between the capacitor  20   1,1  and the diode  34 , receives at the input a control signal equal to {overscore (sc 1,1 )}, complement to 1 of the signal sc 1,1 , where sc 1,1  is the signal shown in FIG.  5 . 
   The component  40  situated on the first group, between the diode  34  and the current source  4 , receives at the input a control signal equal to ({overscore (sc 1,1 )}+{overscore (sc 2,1 )}), where sc 2,1  is the signal shown in FIG.  7  and where the symbol “+” represents the logic operation “or”. 
   The component  42  situated on the third group, between the capacitor  20   2,1  and the diode  36 , receives at the input a control signal equal to sc 2,1 . 
   The component  44  situated on the third group, between the diode  36  and the current source  4 , receives at the input a control signal equal to (sc 1,1 +sc 2,1 ). 
   In this way there is equivalence between this conversion device and that shown in  FIG. 3 , their operation being identical for all the possible configurations of the control signals sc 1,1  and sc 2,1  of the first rank  18   1 . 
   In fact, for the conversion device shown in  FIG. 3 , when sc 1,1 =0 and sc 2,1 =0, the switch  12   1,1  is passing, the switch  14   1,1  is blocked, the switch  12   2,1  is passing and the switch  14   2,1  is blocked. Thus in the first rank  18   1  the current circulates through the first group of switches, directly connecting the current source  4  to the terminal of lower potential of the capacitor  20   1,1 . 
   For the conversion device shown in  FIG. 11 , when sc 1,1 =0 and sc 2,1 =0, {overscore (sc 1,1 )}=1 therefore the switch  38  is passing, {overscore (sc 1,1 )}+{overscore (sc 2,1 )}=1 therefore the switch  40  is passing, sc 2,1 =0 therefore switch  42  is blocked and sc 1,1 +sc 2,1 =0 therefore the switch  44  is blocked. Thus, just as in the preceding case, the terminal of lower potential level of the capacitor  20   1,1  is connected directly to the current source  4  and the current circulates between these two terminals. 
   It will be noted that the current takes the same path through the two energy conversion devices shown in  FIGS. 3 and 11  when sc 1,1 =1 and sc 2,1 =1. 
   It will also be noted that the configuration sc 1,1 =0 and sc 2,1 =1 is an impossible configuration, since it puts the two capacitors  20   1,1  and  20   2,1  of the energy conversion devices of  FIGS. 3 and 11  into short-circuit. 
   Finally, for the energy conversion device shown in  FIG. 3 , when sc 1,1 =1 and sc 2,1 =0 the switch  12   1,1  is blocked, the switch  14   1,1 , is passing, the switch  12   2,1  is passing and the switch  14   2,1  is blocked. Thus the current circulates through the second group in the first rank  18   1 , directly connecting the point situated between the two capacitors  20   1,1  and  20   2,1  and the current source  4 . 
   For the conversion device shown in  FIG. 11 , when sc 1,1 =1 and sc 2,1 =0, {overscore (sc 2,1 )}=0 therefore the switch  38  is blocked, {overscore (sc 1,1 )}+{overscore (sc 2,2 )}=1 therefore the switch  40  is passing, sc 1,1 +sc 2,1 =1 therefore the switch  44  is passing and sc 2,1 =0 therefore the switch  42  is blocked . Thus, as previously, in the first rank  18   1  the current circulates between the point situated between the two capacitors  20   1,1  and  20   2,1  and the current source  4 . However, its path is slightly different from the path followed by the current in the device shown in  FIG. 3 , since it passes through the diode  36  and the switch  44  when it circulates from the point situated between the two capacitors  20   1,1  and  20   2,1  towards the current source  4  and through the closed switch  40  and the diode  34  when it circulates from the current source  4  towards the point situated between the two capacitors  20   1,1  and  20   2,1 . 
   This latter configuration shows that the analogy between the two devices is only possible because they only differ by their rank  18   1  for which there is no capacitor between the switch  14   2,1  (or the switch  12   1,1 ) and the current source. 
   Thus this embodiment permits further reduction in the volume and above all the cost of the conversion device, but the improvement can only be made to the first rank  18   1 . 
   It is clear that a device for conversion of electrical energy according to the invention has the advantage of being less bulky than the conventional multi-cell devices, which extends its field of use to even higher voltage levels. 
   In fact, a conventional device with N=np cells necessitates np−1 capacitors which must be dimensioned so as to support up to 
             (     np   -   1     )     ⁢   E     np     .       
 
On the other hand, a device according to the invention with N=np cells (n stages, p ranks) necessitates n(p−1)=np−n capacitors dimensioned so as to support a voltage which cannot exceed 
             (     p   -   1     )     ⁢   E     np     ,       
 
which is clearly lower than the load referred to in the previous case.
 
   Consequently a device according to the invention has a volume and therefore a price which is less than that of a conventional device with equivalent performance. 
   It will be noted that the invention is not limited to the embodiment described. 
   Thus, as a variant the switches of the intermediate groups of index i with 1&lt;i[n are not necessarily connected in alternate series as described in the chosen embodiment. The switches  12   i,k  and  14   i−1,k  of the i-th intermediate group and of the k-th rank can be connected in parallel. In this case the switches in question must be bidirectional in voltage and unidirectional in current. 
   Equally as a variant, the frequency F is not a multiple of f i  and can even be chosen to be substantially equal to f i  for certain applications.