Abstract:
Electric arc welder ( 10 ) performs a given weld process with selected current waveform performed between electrode ( 24 ) and workpiece ( 26 ). Welder ( 10 ) includes a controller with a digital processor ( 30 ), sensor ( 44 ) for reading instantaneous weld current, and circuit ( 56 ) to convert the instantaneous current into a digital representation of the level of instantaneous weld current. Digital processor ( 30 ) has program circuit ( 64, 66 ) to periodically read and square the digital representation at a given rate, register ( 70, 72 ) for summing a number N of square digital representations to give a summed value, and an algorithm ( 82, 84, 86, 88 ) for periodically dividing the summed value by the number N to provide a quotient and then taking the square root of said quotient to thereby digitally construct rms signal ( 40 ) representing the root mean square of the weld current.

Description:
This application is a continuation of U.S. Ser. No. 10/603,322 filed Jun. 26, 2003 which has since issued as U.S. Pat. No. 7,091,445 on Aug. 15, 2006, which claims priority from U.S. provisional application Ser. No. 60/421,078 filed Oct. 25, 2002. Application Ser. Nos. 10/603,322 and 60/421,078 are incorporated herein by reference in their entireties. 
     The present invention relates to the field of electric arc welding and more particularly to a novel electric arc welder and a system and method for controlling the welding process performed by the welder. 
    
    
     INCORPORATION BY REFERENCE 
     The invention relates to an electric arc welder for performing a welding process between an electrode and a workpiece wherein the welding process is comprised of a succession of current waveforms. Such current waveforms are created by a number of individual current pulses occurring at a frequency of at least 18 kHz with a magnitude of each of the current pulses being controlled by a wave shaper or waveform generator. In this type of electric arc welder, the waveform generator or wave shaper digitally controls a digital pulse width modulator, usually a program in the controller DSP. The pulse width modulator controls the switching of a high speed switching type power source, such as an inverter. This waveform control technology implemented in an electric arc welder has been pioneered by The Lincoln Electric Company of Cleveland, Ohio and is generally disclosed in Blankenship U.S. Pat. No. 5,278,390. The Blankenship patent is incorporated by reference herein as background illustrating a high speed switching power source, such as a inverter, for controlling a weld process including a series of controlled waveforms determined by the output of a waveform generator or wave shaper. 
     The invention involves an embedded algorithm for obtaining the root mean square of either the welding current or the welding voltage, as well as average power. The concept of an embedded system programming of the type used in the present invention is generally disclosed in an article by Jack W. Crinshaw entitled  Embedded Systems Programming  (Integer Square Root) This article published in February 1998 is incorporated by reference herein as illustrating the background technology used in the digital signal programmer of a standard controller associated with an electric arc welder. Also incorporated by reference herein is an article entitled  Electrical Measurements and Heat Input Calculations for GMAW - P Process  dated Nov. 2001. This article teaches away from the present invention and suggests that electric arc welding should be controlled by the average current using a slow sample rate no greater than 4.5 kHz. This article is incorporated by reference illustrating the advantage of the use of the present invention over prior suggestions. 
     BACKGROUND OF THE INVENTION 
     As illustrated in prior patents and literature, electric arc welding has heretofore used the average weld voltage and the average weld current for controlling the operation of the power source in the welder. The digital controller includes a digital signal processor (DSP) for controlling a waveform generator or wave shaper that directs the operation of the normal pulse width modulator. This device creates the waveforms successively used by the welder to perform the welding process. Welders regulate the output current or voltage to an average value such as an average weld current by a feedback loop. For a constant voltage process that is welding in the “spray” region, the average current is an accurate gage of the welding process. However, in pulse welding, the average current and average voltage do not accurately reflect the result of the welding process including the deposition rate, heat zone and penetration. This is explained by a example of an ideal pulse welding process, such as one having 500 amperes for 25% of the time and 100 amperes of background current for 75% of the time has an output current of 200 amperes. However, the average current of the welding process merely indicates the deposition rate and does not reflect the true heat input to the welding operation. Consequently, when the welding process is controlled by a series of repetitive waveforms, such as A.C. welding or pulse welding, average current values can not control the heat input. Recently, the welding processes have become quite complex and now often involve a number of successive waveforms, such as A.C. current and pulse current, so the old technology of feedback control for the welding process is not completely accurate and requires a substantial amount of on-site manipulation by a person knowledgeable in welding, especially a person knowledgeable in the new waveform welding procedure using a welder, such as shown in Blankenship U.S. Pat. No. 5,278,390. With the advent of pulse welding using waveform generators and high speed switching power sources, such as inverters, the obtained weld heat has been adjusted by trial and error. Too much heat causes metal to burn through, especially in thin metal welding. Thus, the welding engineer modulates the average current and average voltage to provide the heat input to the welding process to a level so that burn through is theoretically eliminated. This procedure was applicable, however, only for a pure spray type welding process. This procedure of controlling the heat by the average current and average voltage was not applicable to the new generation of electric arc welders where waveforms are changed to control the welding process. This is the new waveform control technology to which the present invention is directed. The old technology used for non-waveform welding is inapplicable to controlling heat in a controlled waveform type welder. The heat is not known by merely reading the voltage and current when the new waveform type arc welders are employed. Consequently, the welding engineer when using waveform control technology changed the base frequency during pulse welding while maintaining a constant or set average voltage. Using this approach of frequency adjustment of a pulse welding procedure while maintaining a constant voltage, the heat could be adjusted by a trial and error technique. When this trial and error procedure was used to modify the waveforms in a new waveform welder, the heat could, indeed, be controlled; however, it was not precise and involves substantial technical knowledge combined with the trial and error procedures. 
     There is a distinct advantage in pulse welding. This welding process lowers the heat into the joint for the same wire feed speed as a “spray” or “globular” weld process. Thus, a lower heat setting can be set at the factory. The welder had a knob to adjust the nominal frequency, for the purpose indicated above. This change in base frequency did adjust the heat at the welding operation. This resulted in a slight change in the power factor of the welding process through the trial and error method when knowing that the average voltage times average current multiplied by the power factor equals the input heat. Thus, by using a knob to change the base frequency, the power factor was changed to determine heat. However, neither the factory nor the welding engineer at the welding site had the capabilities of directly controlling the power factor. Computation of actual power factor on the fly was not realized in prior control systems and method used for electric arc welders even of the type that used a waveform or wave shape control of the welding process. Consequently, with the introduction of the new waveform welding pioneered by The Lincoln Electric Company, there is a need to control the welding parameters to a value that accurately reflects the heat content. Only in this manner can weld parameters be used in a closed loop feedback system, or otherwise, to control the penetration and heat separately in a weld process using generated waveforms. 
     SUMMARY OF THE INVENTION 
     With the advent of the new wave shapes developed for electric arc welding, the present invention provides a control of the welding parameters to accurately reflect the heating content without use of trial and error procedures or the need for on site welding engineers to modulate and control the welding process. The invention is in welding with a series of generated waveforms, such as A.C. welding or pulse welding. 
     In order to produce a stable weld while continuously feeding wire into the weld puddle, there are primarily two factors that must be balanced. First, the amount of weld metal wire and its material properties determine how much current is needed to melt the wire. Second, the amount of heat determines the heat affected zone or penetration of the welding process. In the past, an operator dialed in a voltage and wire feed speed and manually adjusted the electric stickout to control the amount of heat put into the weld. Welding literature typically claims that the pulse welding process lowers the current for the same deposition rate of a “spray” procedure. This is technically accurate. The average current is, indeed, much less than the average current of an equivalent “spray” procedure when using “pulse” welding. However, the rms currents of both procedures are about the same. The present invention involves the use of rms current for the feedback loop control of the welding process. Thus, the invention involves the use of rms current and rms voltage for controlling the welding process, especially when using a series of generated pulse waves, such as in A.C. welding and “pulse” welding using the technology described in Blankenship U.S. Pat. No. 5,278,390. By using the rms current and rms voltage, a more accurate control of the waveform type welding process is maintained. In accordance with the invention, the rms value and the average value of current and voltage can be used for feedback control. In this aspect of the invention, a first constant is multiplied by the rms value and a second constant is multiplied by the average value of the parameter. These two constants total one, so the constituent of root mean square in the feedback control is adjusted with respect to the constituent of average in the feedback control. These constants preferably total one. In practice, the rms constant is substantially greater than the average value constant so that normally the rms value is predominate over the average value. It has been found that the rms value more accurately reflects the heating value of the welding process. 
     In accordance with a primary aspect of the invention, the feedback control of the electric arc welder maintains the rms voltage and rms currents constant, while adjusting the calculated real time power factor. This procedure of adjusting the power factor adjusts the heat input to the weld procedure to a desired level. 
     Since the rms values of current and voltage are obtained by using the present invention, the power factor can be obtained by calculations within an embedded algorithm in the digital signal processor of the electric arc welder. By maintaining the power factor constant, the electric arc welder will automatically adjust for tolerances experienced in cable impedance at the welding site. By maintaining the power factor constant by using the present invention, the control for the welding process of the electric arc welder can be set at the manufacturing facility by setting the power factor at a given value and the rms current at a given value. When the welder is then installed at the manufacturing facility, the rms current is maintained at the desired constant set at the factory and the power factor is maintained at the set value. The power factor is, thus, accurately controlled at the site. By use of the present invention irrespective of changes in the cable impedance, the welding process will be the same. 
     In the present invention the term “power factor” relates to the power factor of the welding process. This is a parameter obtained by using the present invention through the digital signal processor (DSP) of a welder having an embedded algorithm for calculating the root mean square of both current and voltage. By using the present invention, the power factor is held constant by a closed loop feedback. This feedback system keeps the heat of the welding process at a given selected and desired level. 
     Since the present invention involves the determination of a real time rms value for current arid/or voltage, a closed loop feedback maintains the rms current at a constant desired level. The actual power factor is also generated for a closed loop feedback system so that the welding power factor is adjusted to change the average power and, thus, the heat of the welding operation. Consequently, another aspect of the invention is maintaining the rms current constant while adjusting the power factor to change the heat at the welding process. When this is done in a waveform type welder wherein the waveform is created by a number of current pulses occurring at a frequency of at least 18 kHz with a magnitude of each pulse controlled by a wave shaper, the shape of the waveform in the welding process is modified to adjust the power factor. In this aspect of the invention, the current remains constant. This could not be accomplished in other types of welders, nor in waveform control welders, without use of the present invention. 
     The present invention relates to a control of an electric arc welder of the type wherein a pulse width modulator, normally in the DSP, controls the current waveform constituting the welding process. By using the present invention, the rms current and rms voltage is obtained for the purpose of combining with the average current and average voltage to produce, not only the average power, but also the actual real time power factor. Consequently, the actual power factor can be adjusted, the actual rms current can be adjusted, or the actual rms voltage can be adjusted. In all of these embodiments, the adjustment of the constructed or calculated parameters modifies the waveform to control the welding process accurately in the areas of penetration and heat input. By having the capabilities of the present invention, power factor manipulation adjusts the heat input of the welding process. In accordance with an aspect of the invention, the feedback of current and voltage is a combination of the rms value and the average value in a method or system where the rms value predominates. 
     In pulse welding, the rms current and/or the average current is adjusted to maintain a constant rms voltage. When using the invention for A.C. welding, the output of the welder is regulated to provide a constant rms or a constant rms current. Turning now to a MIG welding process, the output of the machine is regulated to maintain a constant rms current. The basic aspect of the invention is creating a rms current value on a real time basis and/or a rms voltage value on a real time basis. These parameters are regulated by changing the wave shape of the welding process utilizing a standard closed loop feedback system or method. By having the capabilities of creating a rms current, power factor is calculated by the digital signal processor of the arc welder for use in either maintaining a constant power factor or adjustment of the power factor to control heat in a pulse welding process. 
     The invention is primarily applicable for use in an electric arc welder of the type having a pulse shaper or waveform generator to control the shape of the waveform in the welding process. This type of welder has a digitized internal program functioning as a pulse width modulator wherein the current waveform is controlled by the waveform generator or wave shaper as a series of current pulses. The duty cycle of these high speed pulses determines the magnitude of the current at any given position in the constructed waveform of the weld process. This type of welder has a high speed switching power source, such as an inverter. The invention involves the combination of this particular type of power source and implementation of the program and algorithm to form the functions set forth above. 
     In accordance with the invention, there is provided an electric arc welder for performing a given weld process with a selected waveform performed between an electrode and a workpiece. This type of welder generates the waveforms and includes a controller with a digital signal processor. The sensor reads the instantaneous weld current and a circuit converts the instantaneous current into a digital representation of the level of the instantaneous current. The digital processor has a program circuit or other program routine to periodically read and square the digital representation at a given rate. A register in the processor sums a number of squared digital representations to create a summed value. An embedded algorithm in the processor periodically divides the summed value by a number N, which is the number of samples obtained during the sampling process of the waveform. The quotient provided by dividing the summed value by the number of samples is then directed to the algorithm for taking the square root of the quotient to thereby digitally construct an rms signal representing the root mean square of the weld current. This same procedure is used for obtaining the root mean square or rms signal representing the weld voltage. Consequently, the initial aspect of the invention is the use in a waveform welder, a real time signal indicative of the root mean square of the weld current primarily, but also the weld voltage. These signals have not heretofore been obtainable in an arc welder of the type to which the present invention is directed. 
     In accordance with another aspect of the invention, the controller of the specific type of waveform welder defined above includes a feedback control loop with an error detector for generating a current control signal based upon the relationship of two signals. This is a standard closed loop system or method. In performing this system or method, the first of the two signals includes the root mean signal obtained by the first aspect of the present invention. The term “included” is used in this aspect of the invention since a modification of the invention has a feedback using a combination of the root mean value of current or voltage plus a component of the average current and voltage. However, in accordance with an aspect of the invention, the rms value predominates, since it has preferred control characteristics. The use of a feedback with a component of the average current or voltage is a more limited aspect of the present invention. In an aspect of the invention, the contributing component of the root mean square and contributing component of the average is equal to one. The root mean square contribution predominates in accordance with an aspect of the invention. 
     As previously stated, the present invention is directed to an electric arc welder of a specific type wherein a waveform is generated by a waveform generator or wave shaper. Consequently, another aspect of the present invention is the provision of an electric arc welder as defined above wherein the waveform is created by a number of current pulses occurring at a frequency of at least 18 kHz, with a magnitude of each pulse controlled by a wave shaper or waveform generator. The “switching frequency” is the frequency of the pulse width modulator controlling the switching frequency of the power source. This frequency is normally substantially greater than 18 kHz and preferably in the range of 40 kHz. 
     The invention, as defined above, has a sampling rate for the sensed current and/or voltage. In accordance with another aspect of the present invention, this sampling rate is less than 40 kHz or in another aspect it is in the general range of 5 kHz to 100 kHz. In practice, the sampling rate provides a sample each 0.10 ms. It is anticipated that this rate should have a time as low as 0.025 ms. 
     In accordance with an aspect of the invention, there are first and second registers, or buffers, for summing the squared digital representations of either current or voltage. A circuit is controlled by the waveform to generate an event signal T at a given location in the waveform. This event signal T stops the sampling and determines the number N of samples taken. This number N is used in processing either the average current or the rms current. By using two registers, or buffers, the squared value is loaded during each sample of the waveform until the circuit determining the end of the waveform is activated to provide an event signal T. Thus, the present invention utilizes the number of samples N and the event signal T to determine the parameters of a given current waveform. These waveforms are repeated and successively analyzed. At the end of the waveform, as announced by the existence of an event signal T, the digital signal processor utilizes its background time to calculate the rms values and other aspects of the invention as the digital signal processor is performing the normal welding control features of the welder. The algorithm calculations is initiated by the existence or creation of the event signal T. The sample number N is obtained by a digital counter that counts at the sample rate and is reset and read at the signal T. 
     In accordance with still a further aspect of the present invention, there is provided an electric arc welder for performing a given weld process with a selected current waveform performed between an electrode and a workpiece. This welder comprises a controller with a digital signal processor. In accordance with standard technology, the controller has a waveform generator for creating a number of different current pulses occurring at a frequency of at least 18 kHz with a magnitude for each pulse creating the waveform and a feedback current control loop with and error detector program for generating a current control signal based upon the relationship of two input signals. This is essentially waveform technology pioneered by The Lincoln Electric Company. In accordance with the invention, the first input signal includes a rms current signal generated by an algorithm processed by the digital processor. The second signal is a signal representing the desired current or rms signal. Consequently, the desired rms signal selected by the welder manufacturer or adjusted by a welding engineer is tracked by the actual rms current signal of the welder. In this manner, the rms current is held constant. When that occurs, tolerance in the on site cables and other process affecting environmental features are ignored in the welder control scheme. This concept is best used with a calculation of the power factor. Using another aspect of the present invention, the power factor created by using the present invention and the rms current are both maintained constant. Thus, when the welder is programmed at the manufacturing facility with a set rms current and set power factor, these parameters are maintained at the welding operation. Consequently, the welding process at the welding operation duplicates the welding process set into the welder by the welding engineer at the manufacturer of the welder. 
     Still a further aspect of the present invention is the provision of a method of operating an electric arc welder for performing a given weld process with a selected current waveform performed between an electrode and a workpiece. This method involves the process procedure set forth above, wherein the current is sensed and the root mean square current value is calculated as a signal to be used for feedback control of the electric arc welder. This same method is used for obtaining a rms voltage signal used in controlling the electric arc welder of the present invention. Still another aspect of the present invention is the provision of an electric arc welder for performing a given welding process, as defined above. The welder includes a circuit to sample the weld current of the waveform at a give rate, a detector for creating an event signal at a given location in the waveform, a counter to count the number N of samples in successive event signals, a digital processor with an algorithm to calculate a rms value for the weld current based upon the samples taken and the number N counted. The number N and the event signal T have been described in connection with another aspect of the present invention. The invention is used in the sample concept and event signal concept to create values used in an algorithm of a controller for a specific type of electric arc welder. In this manner, the rms value is used to change the waveform to adjust the operation of the waveform welder. The frequency of the switching power source for creating the waveform has an oscillator with a frequency exceeding 18 kHz. Another aspect of the invention is the method of operating the electric arc welder as defined in this aspect of the invention. 
     Another basic aspect of the present invention is the provision of an electric arc welder for performing a given welding process with a selected waveform, as defined above. In this aspect of the invention, the welder comprises a power source with a controller having a digital processor including a program to calculate the real time power factor of the weld current and the weld voltage. The program of this aspect of the invention includes an algorithm to calculate the rms weld voltage, the rms weld current and the average power of the power source. The average power is obtained by using a calculated value for the average current and the average voltage. These average values are obtained by the same sampling arrangement described in accordance with the rms portion of the present invention. The sampling and the number of samples is stopped at an event signal T. Then the current and/or voltage digitized values are added and divided by the number of samples. This provides the average current and average voltage. By multiplying this values together the “average power” is obtained. The concept of obtaining an average power for an electric arc welder is not novel. However, the process of obtaining the average power utilizing the sampling concept and the event signal T is novel in a welder of the type using waveforms that constitute the welding process. 
     In an aspect of the invention, the average power is obtained together with the rms current and the rms voltage. A circuit divides the average power by the rms power to create a signal or level representing the actual real time power factor of the power source. This power factor is compared with the desired power factor to create a corrective value for the wave shaper whereby the actual real time power factor is held at the desired power factor. This maintains a constant power factor. As explained before, by maintaining a constant power factor with a constant rms current, any tolerances in the welding process are overcome so that the welder will operate identically at the site as it did when set up by the manufacturer. This aspect of the invention is primarily employed for pulse welding and changes the shape of the pulse to obtain the desired constant power factor without changing the root mean square current of the welding process. 
     In accordance with another aspect of the invention relating to the obtained power factor level, the power factor is adjustable to change the heat of the welding process, especially when using the invention for pulse welding. The waveform generator or wave shaper controls the shape of the waveform to adjust the power factor to maintain it constant or to adjust it for the purposes of controlling heat. When this adjustment is employed, the rms current is maintained constant. Thus, the power factor is adjusted without adjusting or changing the actual current. The rms current determines the melting rate of the metal. 
     In accordance with another aspect of the present invention there is provided a method of controlling an electric arc welder, of the type defined above, which method comprises calculating the actual power factor of the power source using the rms current and the rms voltage. A desired power factor is then selected for the power source and an error signal is obtained by comparing the actual power factor of the power source to the desired power factor of the power source. This is accomplished by adjusting the waveform by the error signal whereby the actual power factor is held at the desired power factor. 
     The primary object of the present invention is the provision of an electric arc welder of the type using a waveform generator or wave shaper whereby the rms current and/or rms voltage is obtained for controlling the welding process. 
     Still a further object of the present invention is the provision of a welder as defined above which welder is operated in accordance with a method that calculates the rms current and/or the rms voltage and, from this calculation obtains the actual power factor at the welding process. The power factor value controls the heat or maintains a constant power factor for the weld process. 
     Still a further object of the present invention is the provision of an electric arc welder and method of operating the same, which welder and method utilizes existing waveform technology and the common digital signal processor of the welder to calculate rms values and use these values for determining the power factor of the welding process so that these parameters are used in the feedback control systems of the electric arc welder. 
     These and other objects and advantages will become apparent from the following description. 
    
    
     
       BRIEF DESCRIPTION OF DRAWINGS 
       The invention is apparent from the drawings which are: 
         FIG. 1  is a block diagram illustrating an electric arc welder utilizing the present invention for controlling the waveform generator; 
         FIG. 2  is a flow chart and block diagram illustrating the computer program of the digital signal processor utilized for performing the preferred embodiment of the present invention; 
         FIG. 2A  is a cycle chart of digital signal processor utilized for performing the preferred embodiment of the present invention as set forth in  FIG. 2  showing the timing function of the digital signal processor; 
         FIG. 3  is a flow chart of the program for implementing aspects of the cycles in  FIG. 2A  after creation of an event signal T; 
         FIG. 3A  is a waveform graph for the logic applied to the state table in  FIG. 3 ; 
         FIG. 4  is a current waveform graph illustrating the sampling concept used in the present invention to create current signals used in obtaining rms values; 
         FIG. 5  is a block diagram and flow chart of the cycle counter in a field programmable gate array incorporated in the controller and a block diagram of the use of this cycle counter information in the digital signal processor (DSP) to obtain an event signal T; 
         FIG. 5A  is a graph of the pulse current and logic at one terminal of the flow chart shown in  FIG. 5  when pulse welding is used instead of A.C. welding; 
         FIG. 6  is a flow chart of the preferred embodiment of the present invention as performed in the digital signal processor during the cycles show in  FIG. 2A ; 
         FIG. 7  is a block diagram of the program used to create the rms current signal using the present invention; 
         FIG. 8  is a block diagram like  FIG. 7  for creating the rms voltage signal; 
         FIG. 9  is a block diagram showing the aspect of the invention for creating an average power signal; 
         FIG. 10  is a block diagram showing the aspect of the present invention for creating the actual power factor of the welding process for use in the present invention; 
         FIG. 11  is a block diagram of a welder utilizing the power factor value of  FIG. 10  to maintain a constant power factor for the weld process in pulse welding; 
         FIG. 12  is a block diagram, as shown in  FIG. 11 , wherein the power factor value from  FIG. 10  is adjusted manually to control the power factor of the welding process while maintaining the rms current constant; 
         FIG. 13  is a block diagram showing a standard digital filter controlled by the relationship of the actual power factor to the set power factor to adjust the shape of the weld current by adjusting the waveform generator input to maintain a constant power factor; 
         FIG. 14  is a block diagram showing control of the welder by a relationship of average voltage and a rms voltage compared with a set voltage signal to adjust the shape of the waveform to maintain a set voltage; 
         FIG. 15  is a block diagram showing control of the welder by a relationship of average current and a rms current compared with a set current signal to adjust the shape of the waveform to maintain a set current; 
         FIG. 15A  is a current graph showing how the waveform is adjusted to maintain the set value, be it current, voltage or power factor; and, 
         FIG. 16  is a block diagram showing a digital filter to adjust the wire feed speed based upon a comparison of a set voltage to a signal involving a component of average and rms voltage and also a digital filter to adjust the waveform upon a comparison of a set current to a signal involving a component of average and rms current. 
     
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     With reference to  FIG. 1 , electric arc welder  10  is shown in block diagram form. A three-phase rectifier  12  provides power to high speed switching-type power supply  14  across a DC link in the form of input leads  16 ,  18 . In a preferred embodiment, high speed switching-type power supply  14  is an inverter, such as a Power Wave welding power supply available from Lincoln Electric Company of Cleveland, Ohio. However, a high speed switching chopper or other high speed switching-type power supply can also be employed. High speed switching-type power supply  14  performs a preselected welding process. In accordance with present welding technology, high speed switching-type power supply  14  preferably switches at about 18 kHz or higher, and more preferably at 40 kHz or higher. High speed switching-type power supply  14  energizes welding circuit  20  that includes inductor  22  and electrode  24  forming an arc gap with workpiece  26  during performance of the welding operation. Typically, electrode  24  is a forward advancing welding wire from a supply spool. The welding wire is driven toward workpiece  26  at a selected wire speed during performance of the welding operation. 
     Controller  30  controls high speed switching-type power supply  14  during the welding operation. In accordance with the present welding technology, controller  30  is a digital device including waveform generator  32  that outputs power level waveform  34  represented by a line that is the input to pulse width modulator  36 . Pulse width modulator  36  produces pulse train  38  (represented by a line) of pulses with pulse widths corresponding to the power level of waveform  34 . In other words, waveform  34  is converted into pulse width modulated pulse train signal  38  by pulse width modulator  36 . Pulse width modulator  36  produces pulses of controlled width at a frequency preferably above 18 kHz, and more preferably about 40 kHz or higher, which is the input to high speed switching-type power supply  14 . The power supply switching is controlled by pulse -width modulated pulse train  38  to energize welding circuit  20  in accordance with power level waveform  34 . 
     Waveform  34  implements a desired welding process. Typically, a welding process is made up of a waveform train of repeating waveforms. For pulse welding, power level waveform  34  has a preselected wave shape for generating a welding process pulse. The average power or true heat produced in the welding process implemented by waveform  34  over a time interval [T 1 , T 2 ] is given by: 
                       P   avg     =       1       T   2     -     T   1         ⁢       ∫     T   1       T   2       ⁢         v   ⁡     (   t   )       ·     i   ⁡     (   t   )         ⁢           ⁢     ⅆ   t             ,           (   1   )               
where P avg  is the average power, v(t) is the instantaneous voltage, i(t) is the instantaneous welding current, v(t)·i(t) is the instantaneous power, and T 1  and T 2  are the starting and ending time points of the time interval, respectively, of the integration. In the case of a substantially periodic waveform, the average power can be expressed in terms of root-mean-square (rms) voltage and rms current according to:
   P   avg   =V   rms   ·I   rms   ·PF   (2), 
where the rms voltage, V rms , and rms current, I rms , are given by:
 
                       V   rms     =           ∫     T   1       T   2       ⁢         [     v   ⁡     (   t   )       ]     2     ⁢           ⁢     ⅆ   t             T   2     -     T   1             ,     
     ⁢       I   rms     =             ∫     T   1       T   2       ⁢       [     i   ⁡     (   t   )       ]     2       ⁢                 T   2     -     T   1             ,           (   3   )               
respectively, and PF is the power factor. In computing the average power and the rms current and voltage values for waveform  34  that implements pulse welding, the time interval [T 1 , T 2 ] preferably corresponds to one pulse or a plurality of pulses. In waveform-controlled welding, the pulse time interval may vary for successive pulses. Hence, in the described preferred embodiment, the starting and stopping times T 1  and T 2  are extracted from waveform  34  as event signals T determined from a characteristic feature of waveform  34 .
 
     Equation (3) can be rewritten to define the power factor PF according to: 
                   PF   =         P   avg         V   rms     ·     I   rms         .             (   4   )               
There is in general a close relationship for substantially any waveform  34  between the rms voltage and current values and the average power.
 
     In contrast, the average voltage, V avg , and average current, I avg , given by: 
                       V   avg     =         ∫     T   1       T   2       ⁢       v   ⁡     (   t   )       ⁢           ⁢     ⅆ   t             T   2     -     T   1           ,     
     ⁢       I   avg     =         ∫     T   1       T   2       ⁢       i   ⁡     (   t   )       ⁢           ⁢     ⅆ   t             T   2     -     T   1           ,           (   5   )               
have a close relationship with the average power only for certain waveforms, such as are used in constant-voltage “spray” type welding. However, if, for example, the waveform includes a stepped pulse that is 500 amperes for 25% of the time and 100 amperes for 75% of the time, the rms value is 265 amperes, while the average value is 200 amperes. In this case, the rms values provide a more accurate true heat value.
 
     With continuing reference to  FIG. 1 , controller  30  of electric arc welder  10  implements an exemplary pulse welding process in which the magnitude of waveform  34  is controlled using an rms current  40  that is calculated from an instantaneous welding current I a    42  measured across shunt  44 . In the constant current welding process shown in  FIG. 1 , rms current  40  is compared with set rms current  46  by digital error amplifier  48  to produce error signal  50  that controls an amplitude of waveform  34  to maintain a constant rms current. Similarly, for a constant voltage welding process, control is suitably based on an rms voltage calculated from instantaneous welding voltage V a    52  measured across the weld by voltmeter  54 . 
     With reference to  FIG. 2 , computation of the rms current from instantaneous welding current I a    42  includes processing with analog-to-digital converter  56  to produce digitized instantaneous current  58 , which is the input to digital signal processing block  60 . Digital signal processing block  60  performs the current squared integration of Equation (3) digitally as a Riemann sum, dividing the current into time intervals Δt defined by oscillator  62  for the summing. The digitizing interval Δt for the Riemann sum is suitably about 0.1 milliseconds to provide adequate samples for each pulse or repetition of waveform  34 . Sample-and-hold circuit  64  holds the digitized current for the period Δt, and squaring processor  66  computes the square of the held current value. 
     In order to enable continuous summation of rms current in parallel with related processing such as the computation of the square-root operation of Equation (3), the summing preferably employs two alternating storage buffers, namely first buffer  70  (identified as Buffer A), and second buffer  72  (identified as Buffer B). Values are stored in the active buffer at intervals  76 ,  78  that are preferably in a range of about 0.025-0.100 milliseconds. When first buffer  70  is active, switch  80  transfers values at time intervals Δt to first buffer  70 , which accumulates the current-squared values and also maintains a sample count N of a number of accumulated current samples. As a background process during accumulation in first buffer  70 , the contents of second buffer  72  are processed by division processor  82  to divide by the number of samples N, and by square-root processor  84  to complete computation of the root-mean-square calculation of Equation (3). 
     At a selected event signal T generated by a characteristic of waveform  34 , the operation of buffers  70 ,  72  switches. Second accumulator  72  is cleared, and switch  80  subsequently transfers current-squared samples into second accumulator  72 . As a background process during accumulation in second buffer  72 , the contents of first buffer  70  are processed by division processor  86  to divide by the number of samples N, and by square-root processor  88  to complete computation of the root-mean-square calculation of Equation (3). 
       FIG. 7  shows a simplified block diagram of digital signal processing block  60 , which omits the details of the alternating summation buffers  70 ,  72  and related switching circuitry that are shown in detail in  FIG. 2 . In  FIG. 7 , current-squaring block  66 , switch  80 , and alternating summation blocks  70 , 72  are represented by a single summation block  100  that sums current-squared samples between occurrences of the event signal T triggered by a characteristic of waveform  34 , and also maintains the count N of the number of accumulated samples. Division background processes  82 ,  86  of  FIG. 2  are represented by a single normalization background process  102  in  FIG. 7 . Square-root background processes  84 ,  88  of  FIG. 2  are represented by a single square root background process  104  in  FIG. 7 . 
     With reference to  FIG. 8 , it will be appreciated that digital signal processing block  60  shown in  FIG. 2  and represented in simplified form in  FIG. 7  is readily adapted to perform rms voltage calculations, by replacing measured instantaneous current I a    42  with instantaneous voltage V a    52  measured by voltmeter  54  of  FIG. 1 .  FIG. 8  shows rms voltage digital signal processing block  60 ′ in a simplified form analogous to the simplified form of  FIG. 7 . The digitized voltage is processed by sample-and-hold circuit  64 ′ which holds the digitized voltage for the period Δt. Voltage-squared summation block  100 ′ sums voltage-squared samples and maintains a count N of the number of accumulated voltage samples. Preferably, summation block  100 ′ uses alternating summation buffers analogous to buffers  70 ,  72  shown for the current-squared summation in  FIG. 2 . Normalization background process  102 ′ divides the voltage-squared sample sum by the number of samples N. Square root background process  104 ′ takes the square root to complete implementation of the rms voltage V rms  mathematically shown in Equation (3). 
     With reference to  FIG. 9 , it will be appreciated that digital signal processing block  60  shown in  FIG. 2  and represented in simplified form in  FIG. 7  is similarly readily adapted to perform average power calculations, by inputting both measured instantaneous current I a    42  and measured instantaneous voltage V a    52 .  FIG. 9  shows average power digital signal processing block  60 ″ in a simplified form analogous to the simplified form of  FIG. 7 . Sample-and-hold circuits  64 ,  64 ′ which hold the digitized current and voltage, respectively, for the period Δt, are accessed by current-times-voltage summation block  100 ″ which sums current-times-voltage samples and maintains a count N of the number of accumulated current-times-voltage samples. Preferably, summation block  100 ″ uses alternating summation buffers analogous to buffers  70 ,  72  shown for the current-squared summation in  FIG. 2 . Normalization background process  102 ″ divides the current-times-voltage sample sum by the number of samples N to produce the average power P avg  shown mathematically in Equation (1). 
     Digital signal processing blocks  60 ,  60 ′,  60 ″ compute the rms current, the rms voltage, and the average power as Riemann sums.  FIG. 4  shows exemplary current waveform  120  that is digitally sampled. Each digital sample is represented by a rectangular sample bar  122  of time duration Δt and height corresponding to the digitized value of current waveform  120  held by sample-and-hold circuit  64  at the time interval Δt. 
     Digital signal processing blocks  60 ,  60 ′,  60 ″ are optionally implemented as separate processing pathways that execute in parallel. However, in a preferred embodiment digital signal processing blocks  60 ,  60 ′,  60 ″ use some common digital signal processing blocks into which the sampled voltage and current signals are time-domain multiplexed. Such a multiplexing approach reduces the amount of circuitry required. Each summation (voltage-squared, current-squared, and voltage-times-current) has its own alternating summation buffer set (for example, summation buffer set  70 ,  72  for summing current-squared values as shown in  FIG. 2 ). 
     With reference to  FIG. 2A , a suitable process cycling for the time-domain multiplexing is shown. The process cycling employs four cycles  130 ,  132 ,  134 ,  136  each occupying one-fourth of the sampling period Δt. For the exemplary Δt equal 0.1 millisecond, each of the four cycles  130 ,  132 ,  134 ,  136  occupies 0.025 milliseconds, During first cycle  130 , the voltage V a  and current I a  are digitized and sample/held. During second cycle  132 , the current-squared is computed and added to the current-squared summation. During third cycle  134 , the voltage-squared is computed and added to the voltage-squared summation. During fourth cycle  136 , a check is performed to determine whether an event signal T has been detected, and the sample count is incremented. Moreover, throughout the cycling other processing, such as computation of the square roots of values stored in the inactive summation buffers, can be performed as background processes. Similarly, digital signal processing welding control operations, such as waveform shaping described by Blankenship U.S. Pat. No. 5,278,390, can be performed as background control processes during the cycling. 
     With reference to  FIGS. 2 and 2A , and with further reference to  FIG. 3A  and  FIG. 6 , the cycling as applied to the current-squared calculation is described.  FIG. 3A  illustrates current waveform  34  extending between first event signal T 1  and second event signal T 2 . Event signals T 1 , T 2  are suitably generated by a circuit controlled by waveform  34 . In  FIG. 3A , the circuit generates event signal T 1  responsive to onset of the rising edge of current pulse  140 , and the circuit generates event signal T 2  responsive to onset of the rising edge of current pulse  142 . Thus, there is a current pulse between each two successive event signals T. Rather than detecting the rising edge, the event signals can instead be generated by detecting another characteristic of the pulse, such as the falling edge of the current pulse. 
     During the time interval between event signal T 1  and event signal T 2 , current-squared samples are accumulated in summation buffer  70 , as indicated in  FIG. 3A  by the notation “Adding to Buffer A”. Each occurrence of second cycle  132  of  FIG. 2A  adds another current-squared sample to buffer  70 . Although not shown in  FIGS. 2 ,  3 A, or  6 , voltage-squared samples and average power samples are preferably being accumulated in their respective buffers during the other cycles of the four-cycle process of  FIG. 2A . Detection of event signal T 2  is indicated by detection block  150  of  FIG. 6 . Responsive to detection  150 , buffers  70 ,  72  are switched so that buffer  72  is used to accumulate current-squared samples of next pulse  142  of waveform  34 , while buffer  70  in which the current-squared samples of pulse  140  are accumulated is shifted  152  into the background. In background processing, the current-squared sum is divided  154  by the number of samples N and the square-root is taken  156  to complete the rms algorithm. The computed rms current value for pulse  140  is written  158  to a register for use in welding process control. 
     With reference to  FIG. 5 , a suitable method for generating event signals T is described. A field programmable gate array (FPGA) includes cycle counter state machine  170  that updates two-bit counter  172 . State machine  170  is configured to increment two-bit counter  172  each time the state changes. Each change of state corresponds to an occurrence of event signal T. In the digital signal processing (DSP), two-bit comparator  174  compares the value of two-bit counter  172  with previous counter value register  176  during fourth cycle  136  of  FIG. 2A . A change in the value of two-bit counter  172  indicated by the comparison corresponds to an occurrence of event signal T. Responsive to event signal T, digital gate  178  loads the new value of two-bit counter  172  into previous counter value register  176 . In this arrangement, the value stored in two-bit counter  172  is not significant; rather, a change in the counter value is detected. 
     With continuing reference to  FIG. 5  and with further reference to  FIG. 5A , the polarity of waveform  34  along with an auxiliary “Misc2” signal are input to state machine  170  through “OR” gate  174 . This arrangement enables the FPGA to generate event signals T for pulse welding and for a.c. welding. In the case of a.c. welding, Misc 2  is set to zero so that the polarity signal feeds through to cycle counter state machine  170 . For pulse welding, Misc 2  is set to one when the arc is shorted, and zero when the arc is not shorted.  FIG. 5A  shows a graph of pulse current  180  and the value of Misc 2   182  when pulse welding is used instead of A.C. welding. 
     With continuing reference to  FIG. 5  and with further reference to  FIG. 3 , events initiated by an occurrence of event signal T are described. At fourth cycle  136  of  FIG. 2A , the digital signal processing performs a check  190  to see if an occurrence of event signal T has been detected. This is done by comparing the current value of two-bit counter  172  with stored counter value  176  using two-bit comparator  174 . If no change in counter value has occurred, the digital signal processing continues to loop through the four states  130 ,  132 ,  134 ,  136  of  FIG. 2A . However, if check  190  detects an occurrence of event signal T, the rms value is computed  192  as set forth in Equation (3) and in accordance with  FIGS. 2 and 7 . Computation  192  is a background digital signal process. Additionally, a buffer switch  194  is performed so that whichever buffer (buffer A  70  or buffer B  72 ) had been active is switched to the background, and whichever buffer (buffer B  72  or buffer A  70 ) had been the background buffer is made the active accumulation buffer. 
     Exemplary digital signal processing circuitry and associated FPGA circuitry for substantially real-time computation of rms voltage V rms , rms current I rms , and average power P avg  have been described with reference to  FIGS. 1-9 . The described digital signal processing circuitry implements Equations (1) and (3) using Riemann sums, and is exemplary only. Those skilled in the art can readily modify the illustrated digital circuitry or substitute other digital circuitry to perform these computations or substantial equivalents thereof. The illustrated circuitry provides certain features that may be optionally omitted or modified. For example, separate and independent digital signal processing pathways can be provided for computing each of the rms voltage V rms , rms current I rms , and average power P avg  values. In this arrangement, time-domain multiplexing aspects of the circuitry can be omitted. Rather than having two alternating accumulators, a single accumulator can be employed in conjunction with a storage register that stores the previous sum for background normalization/square root processing. Moreover, if the digital signal processing is sufficiently fast or if parallel processing is employed, the temporary storage may be omitted entirely, and the normalization/square root processing performed substantially in real time for intervals between successive event signals T. Still further, a trapezoidal or otherwise-shaped integral element can be substituted for rectangular sample bars  122  of the Riemann sum illustrated in  FIG. 4 . Those skilled in the art can make other modifications to the exemplary digital signal processing and FPGA circuitry illustrated herein for implementing Equations (1) and (3) as digital circuitry. 
     With reference to  FIG. 10 , digital signal processing block  200  computes the power factor (PF) in accordance with Equation (4) from the rms voltage V rms , rms current I rms , and average power P avg  values. The denominator of Equation (4) is computed using multiplier  202  acting on the rms current I rms  and rms voltage V rms  output by digital signal processing blocks  60 ,  60 ′ of  FIGS. 7 and 8 , respectively. The average power P avg  output by digital signal processing bloc  60 ″ of  FIG. 9  is divided by this denominator using division block  204  to compute the power factor PF. 
     With continuing reference to  FIG. 10  and with further reference to  FIG. 11 , electric arc welder  10  of  FIG. 1  is readily adapted to implement a constant power factor control of the weld process in pulse welding. Controller  30 ′ is a modified version of controller  30  of  FIG. 1 . Digital error amplifier  48 ′ produces error signal  50 ′ based on the power factor PF. Digital error amplifier  48 ′ compares the power factor PF output by digital signal processing block  200  (shown in detail in  FIG. 10 ) with PF set value  46 ′. Waveform generator  32 ′ modifies selected waveform shape  210  based on error signal  50 ′ as described in Blankenship U.S. Pat. No. 5,278,390 which is incorporated by reference herein. 
     With continuing reference to  FIG. 10  and with further reference to  FIG. 12 , electric arc welder  10  of  FIG. 1  is similarly readily adapted to implement a constant current welding process in which heat input to the weld is controlled by adjusting the power factor PF. Controller  30 ″ is a modified version of controller  30  of  FIG. 1 . The rms current  40  is compared with set rms current  46  by digital error amplifier  48  to produce current error signal  50  as in  FIG. 1 . Additionally, a second digital error amplifier  220  produces power factor error signal  222  by comparing the power factor PF output by digital signal processing block  200  (shown in detail in  FIG. 10 ) with adjustable welding heat set value  224 . Waveform generator  32 ″ modifies selected waveform shape  210  based on error signals  50 ,  222  as described in Blankenship U.S. Pat. No. 5,278,390. 
     With reference returning to  FIG. 11  and with further reference to  FIG. 13 , in digital error amplifier  48 ′ the power factor error signal optionally incorporates digital filtering. As shown in  FIG. 13 , digital error amplifier  48 ′ includes difference operator  232  that computes difference signal  234  which is proportional to a difference between the computed power factor and power factor set value  46 ′. Difference value  234  is input into digital filter  236  which generates control signal  50 ′ for adjusting the waveform shape in accordance with the method described in Blankenship U.S. Pat. No. 5,278,390. In one suitable embodiment, digital filter  236  is an infinite impulse response filter. The digital filter can be used to amplify the signal, smooth the signal, remove high frequency signal components, or otherwise adjust the control signal. 
     With reference to  FIG. 14 , a digital error amplifier  240  for constant voltage control is shown. Digital error amplifier  240  includes difference operator  242  that computes difference signal E(n)  246  given by:
 
 E ( n )= V   set −( a·V   avg   +b·V   rms )  (6),
 
where V set  is a set voltage value, V avg  is an average voltage value computed in accordance with Equation (5), a is an average voltage weighting factor implemented by multiplier  250 , V rms  is the rms voltage of Equation (3) that is output by digital signal processing block  60 ′ of  FIG. 8 , and b is an rms voltage weighting factor implemented by multiplier  252 . It will be recognized that difference signal E(n)  246  can be biased by adjusting the weighting factors a and b toward average voltage control, rms voltage control, or a selected weighted combination of average voltage and rms voltage control. Because the rms voltage is typically a better measure of the true heat input to the weld by the welding process, the rms weight b is preferably greater than the average weight a, that is, b&gt;a. Moreover, the sum of the weighting factors is preferably unity, that is, a+b=1. Optionally, difference signal E(n)  246  is processed by digital filter  254 , such as an infinite impulse response filter, to amplify, smooth, or otherwise manipulate difference signal E(n)  246  to produce control signal  256  for adjusting the waveform shape in accordance with the method described in Blankenship U.S. Pat. No. 5,278,390.
 
     With reference to  FIG. 15 , a digital error amplifier  260  for constant current control is shown. Digital error amplifier  260  includes difference operator  262  that computes difference signal E(n)  266  given by:
 
 E ( n )= I   set −( a·I   avg   +b·I   rms )  (7),
 
where I set  is a set current value, I avg  is an average current value computed in accordance with Equation (5), a is an average current weighting factor implemented by multiplier  270 , I rms  is the rms current of Equation (3) that is output by digital signal processing block  60  of  FIG. 7 , and b is an rms current weighting factor implemented by multiplier  272 . It will be recognized that difference signal E(n)  266  can be biased by adjusting the weighting factors a and b toward average current control, rms current control, or a selected weighted combination of average current and rms current control. Because the rms current is typically a better measure of the true heat input to the weld by the welding process, the rms weight b is preferably greater than the average weight a, that is, b&gt;a. Moreover, the sum of the weighting factors is preferably unity, that is, a+b=1. Optionally, difference signal E(n)  266  is processed by digital filter  274 , such as an infinite impulse response filter, to amplify, smooth, or otherwise manipulate difference signal E(n)  266  to produce control signal  276  for adjusting the waveform shape in accordance with the method described in Blankenship U.S. Pat. No. 5,278,390.
 
     With reference to  FIG. 15A , an exemplary waveform shape adjustment in accordance with the waveform shape adjustment method of Blankenship U.S. Pat. No. 5,278,390 is illustrated. Two waveforms  280 ,  282  are shown in solid and dashed lines, respectively. For b=1 and a=0 in Equation (6) or Equation (7) (for voltage control or current control, respectively), waveforms  280 ,  282  have equal rms values. However, the average value is generally different for waveforms  280 ,  282 .Compared with waveform  280 , waveform  282  has a reduced voltage or current background magnitude and an increased voltage or current magnitude in the pulse. 
     Moreover, it will be appreciated that the pulse repetition period of waveforms  280 ,  282  may be different. This difference in repetition period is accounted for in the digital signal processing by performing the Riemann sums of Equations (1), (3), and (5) over intervals between successive event signals T, instead of performing the Riemann summing over time intervals of fixed length. Generating event signals T at a rising pulse edge or other identifiable characteristic of the waveform allows the summation interval to track the repetition period of the waveform as the repetition period is adjusted by the waveform shaping. 
     With reference to  FIG. 16 , two digital error amplifiers  300 ,  302  compute current and voltage error signals for use in a constant current, constant voltage welding process control. Digital error amplifier  300  includes difference operator  310 , weighting factors a  312  and b  314 , and digital filter  316 . Digital error amplifier  300  has the same voltage inputs and general circuit topology as amplifier  240  of  FIG. 14 ; however, digital error amplifier  300  produces control signal  318  for controlling wire feed speed during the welding process. With increasing output of amplifier  300  the wire feed speed should be decreased, while with decreasing output of amplifier  300  the wire feed speed should be increased. Digital amplifier  302  includes difference operator  330 , weighting factors c  332  and d  334 , and digital filter  336 . Digital error amplifier  302  has the same current inputs and general circuit topology as amplifier  260  of  FIG. 15 , and produces control output  338  for adjusting the waveform shape in accordance with the method described in Blankenship U.S. Pat. No. 5,278,390. Hence, the waveform shape and the wire feed speed are simultaneously controlled using digital error amplifiers  300 ,  302  to keep both voltage and current constant. 
     The invention has been described with reference to the preferred embodiments. Obviously, modifications and alterations will occur to others upon reading and understanding the preceding detailed description. It is intended that the invention be construed as including all such modifications and alterations insofar as they come within the scope of the appended claims or the equivalents thereof.