Abstract:
An output buffer circuit includes, a voltage-to-current conversion circuit for converting a voltage at an output terminal into a first current supplied from a first power supply terminal, a current-to-current conversion circuit for converting the first current into a second current flowing between the output terminal and a second power supply terminal, and a control circuit for turning ON and OFF said current-to-current circuit in accordance with an input voltage at an input terminal.

Description:
BACKGROUND OF THE INVENTION 
     1. Field of the Invention 
     The present invention relates to an output buffer circuit connectable to a small computer system interface (SCSI) cable. 
     2. Description of the Related Art 
     A prior art output buffer circuit of an open drain output type output buffer circuit is comprised of an N-channel MOS transistor having a gate connected to an input terminal, a drain connected to an output terminal, and a source connected to a ground terminal. Also, a SCSI cable is connected to the output terminal of the output buffer circuit. In this case, terminal resistors are connected to each end of the SCSI cable. Further, in accordance with the SCSI standard, the gate width/gate length of the transistor must be sufficiently large. This will be explained later in detail. 
     In the above-mentioned prior art open drain type output buffer circuit, however, when the transistor is turned ON, an instantaneously large current appears in a sink current flowing through the transistor. This large current affects the output voltage. That is, a counter electromotive force due to the instantaneously large sink current makes the output voltage ring. This ringing phenomenon propagates error signals on the SCSI cable, which is a large problem in high speed data transfer for large capacity data. 
     A prior art output buffer of a tri-state type is comprised of a P-channel MOS transistor and an N-channel MOS transistor connected between a power supply terminal and a ground terminal. Also, in accordance with the SCSI standard, the gate width/gate length of each transistor must be sufficiently large. This will also be explained later in detail. 
     Even in the above-mentioned prior art tri-state output buffer circuit, when the N-channel transistor is turned ON, an instantaneously large current appears in a sink current flowing through the N-channel transistor, in the same way as in the open drain type output buffer circuit. In addition, when the P-channel transistor is turned ON, an instantaneously large current appears in a drive current flowing through the P-channel transistor. These large currents affect the output voltage. That is, a counter electromotive force due to the instantaneously large currents makes the output voltage ring. This ringing phenomenon propagates error signals on the SCSI cable, which is also a large problem in high speed data transfer for large capacity data. 
     SUMMARY OF THE INVENTION 
     It is an object of the present invention to suppress the ringing phenomenon in an output voltage of an output buffer circuit connectable to a SCSI cable. 
     According to the present invention, an output buffer circuit includes a voltage-to-current conversion circuit for converting a voltage at an output terminal into a first current supplied from a first power supply terminal, a current-to-current conversion circuit for converting the first current into a second current flowing between the output terminal and a second power supply terminal, and a control circuit for turning ON and OFF said current-to-current circuit in accordance with an input voltage at an input terminal. 
    
    
     BRIEF DESCRIPTION OF THE DRAWINGS 
     The present invention will be more clearly understood from the description as set forth below, as compared with the prior art, with reference to the accompanying drawings, wherein: 
     FIG. 1 is a circuit diagram illustrating a first prior art output buffer circuit; 
     FIG. 2 is a graph showing an example of the output voltage to sink current characteristics of the transistor of FIG. 1; 
     FIGS. 3A, 3B and 3C are graphs showing the operation of the output buffer circuit of FIG. 1; 
     FIG. 4 is a circuit diagram illustrating a second prior art output buffer circuit; 
     FIG. 5A is a graph showing an example of the output voltage to sink current characteristics of the N-channel transistor of FIG. 4; 
     FIG. 5B is a graph showing an example of the output voltage to drive current characteristics of the P-channel transistor of FIG. 4; 
     FIGS. 6A, 6B, 6C and 6D are graphs showing the operation of the output buffer circuit of FIG. 4; 
     FIG. 7 is a circuit diagram illustrating a first embodiment of the output buffer circuit according to the present invention; 
     FIG. 8A is a graph showing an example of the output voltage to drain current characteristics of one transistor of FIG. 7; 
     FIG. 8B is a graph showing an example of the output voltage to drain voltage characteristics of the one transistor of FIG. 7; 
     FIG. 9A is a graph showing an example of the output voltage to drain current characteristics of another transistor of FIG. 7; 
     FIG. 9B is a graph showing an example of the output voltage to drain voltage characteristics of the another transistor of FIG. 7; 
     FIG. 10 is a graph showing an example of the output voltage to sink current characteristics of the one transistor of FIG. 7; 
     FIGS. 11A, 11B and 11C are graphs showing the operation of the output buffer circuit of FIG. 7; 
     FIG. 12 is a circuit diagram illustrating a second embodiment of the output buffer circuit according to the present invention; 
     FIG. 13A is a graph showing an example of the output voltage to sink current characteristics of the transistor of FIG. 12; 
     FIG. 13B is a graph showing an example of the output voltage to drive current characteristics of the transistor of FIG. 12; and 
     FIGS. 14A, 14B, 14C and 14D are graphs showing the operation of the output buffer circuit of FIG. 12. 
    
    
     DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     Before the description of the preferred embodiments, prior art output buffer circuits will be explained with reference to FIGS. 1, 2, 3A, 3B, 3C, 4, 5A, 5B, 6A, 6B, 6C and 6D. 
     In FIG. 1, which illustrates a first prior art output buffer circuit, an open drain output type output buffer circuit 1-A is provided. That is, the output buffer circuit 1-A is comprised of an N-channel MOS transistor 101 having a gate connected to an input terminal IN, a drain connected to an output terminal OUT, and a source connected to a ground terminal. 
     A SCSI cable 2 is connected to the output terminal OUT of the output buffer circuit 1-A. In this case, terminal resistors 31 and 32 are connected to one end of the SCSI cable 2, and terminal resistors 33 and 34 are connected to the other end of the SCSI cable 2. 
     In accordance with the SCSI standard, when an output voltage V OUT  at the output terminal OUT is 0.5V, a sink current I S  flowing through the transistor 101 is required to be not smaller than 48 mA. Generally, an example of output voltage to sink current characteristics of the transistor 101 is shown in FIG. 2. For realizing this, the transistor 101 has to be sufficiently large in scale; for example, its gate width/gate length is 2000 to 3000 μm/1 μm. 
     The operation of the output buffer circuit 1-A of FIG. 1 is explained next with reference to FIGS. 3A, 3B and 3C. 
     When an input voltage V IN  at the input terminal IN is changed as shown in FIG. 3A, an instantaneously large current indicated by X in FIG. 3B appears in the sink current I S  flowing though the transistor 101 due to the small ON resistance thereof. Such a large sink current I S  is represented by 
     
         I.sub.S =C·dV.sub.OUT /dt                         (1) 
    
     where C is an equivalent capacitance of the SCSI cable 2. Therefore, if the equivalent capacitance C is 200 pF, a power supply voltage V DD  is 5V, and a through rate of the output voltage V OUT  is 5 ns, then, ##EQU1## 
     The large sink current I S  as indicated by X in FIG. 3B affects the output voltage V OUT  as shown in FIG. 3C. That is, a counter electromotive force due to the spontaneously large sink current I S  makes the output voltage V OUT  ring as indicated by Y in FIG. 3C. In this case, the counter electromotive force V is represented by 
     
         V=-LdI/dt                                                  (2) 
    
     where L is an inductance of the SCSI cable 2. Therefore, if L is 10 nH and the through rate of the output voltage V OUT  is also 5 ns, then, ##EQU2## 
     This ringing phenomenon as indicated by Y in FIG. 3C propagates error signals on the SCSI cable 2, which is a large problem in high speed data transfer for large capacity data. 
     In FIG. 4, which illustrates a second prior art output buffer circuit, a tri-state type output buffer circuit 1-B is provided. That is, an enable terminal EN is provided. Also, the output buffer circuit 1-B is comprised of an N-channel MOS transistor 201 corresponding to the transistor 101 of FIG. 1, a P-channel MOS transistor 202, an N-channel MOS transistor 203, a P-channel MOS transistor 204, and an inverter 205. The transistors 201 and 202 are controlled by the input voltage V IN , and the transistors 203 and 204 are controlled by an enable voltage V EN  at the enable terminal EN. 
     Also, in accordance with the SCSI standard, when the output voltage V OUT  at the output terminal OUT is 0.5V, the sink current I S  flowing through the transistor 201 is required to be not smaller than 48 mA. Generally, an example of output voltage to sink current characteristics of the transistor 201 where the transistor 203 is turned ON is as shown in FIG. 5A. For this purpose, the transistor 201 as well as the transistor 203 has to be sufficiently large in scale; for example, its gate width/gate length is 2000 to 3000 μm/1 μm. 
     Similarly, when the output voltage V OUT  at the output terminal OUT is high, for example, V DD  -0.5V, a drive current I D  flowing through the transistor 202 is required to be large for charging the capacitance of the SCSI cable 2. Generally, an example of output voltage to drive current characteristics of the transistor 202 where the transistor 204 is turned ON is shown in FIG. 5B. For this purpose, the transistor 202 as well as the transistor 204 has to be sufficiently large in scale. 
     The operation of the output buffer circuit 1-B of FIG. 4 is explained next with reference to FIGS. 6A, 6B, 6C and 6D. 
     As shown in FIG. 6A, assume that an enable signal V EN  at the enable terminal EN is V DD  (=5V). 
     When the input voltage V IN  at the input terminal IN is changed as shown in FIG. 6B, an instantaneously large current indicated by X1 in FIG. 6C appears in the sink current I S  flowing though the transistor 201 due to the small ON resistance thereof. Such a large sink current I S  is, for example, 200 mA, in the same way as in the output buffer circuit 1-A of FIG. 1. Also, the large sink current I S  as indicated by X1 in FIG. 6C affects the output voltage V OUT  as shown in FIG. 6D. That is, the output voltage V OUT  rings as indicated by Y1 in FIG. 6D. 
     Simultaneously, an instantaneously large current indicated by X2 in FIG. 6C appears in the drive current I D  flowing though the transistor 202 due to the small ON resistance thereof. Such a large drive current I D  is, also, 200 mA. This large drive current I D  as indicated by X2 in FIG. 6C also affects the output voltage V OUT  as shown in FIG. 6D. That is, the output voltage V OUT  rings as indicated by Y2 in FIG. 6D. 
     The ringing phenomenon as indicated by Y1 and Y2 in FIG. 6D propagates error signals on the SCSI cable 2, which is a large problem in high speed data transfer for large capacity data. 
     In FIG. 7, which illustrates a first embodiment of the present invention, an open drain type output buffer circuit 1-C corresponding to the output buffer circuit 1-A of FIG. 1 is provided. That is, the output buffer circuit 1-C is comprised of a P-channel MOS transistor 301 having a source connected to the power supply voltage terminal V DD  and a gate connected to the output terminal OUT. The transistor 301 converts the output voltage V OUT  into a drain current I 1 . 
     An N-channel MOS transistor 302 is connected between the drain of the transistor 301 and the ground terminal GND. Also, an N-channel MOS transistor 303 is connected between the output terminal OUT and the ground terminal GND. The gate of the transistor 302 is connected to the gate of the transistor 303, and therefore, the transistors 302 and 303 form a current mirror circuit. Also, the size of the transistor 303 is larger than that of the transistor 302, thus enabling a current amplification. Note that the transistor 303 corresponds to the transistor 101 of FIG. 1. 
     In order to control the voltages of the gates of the transistors 302 and 303, a transfer gate formed by a P-channel MOS transistor 304 and an N-channel MOS transistor 305 is connected between the drain of the transistor 301 and the gates of the transistors 302 and 303, and a transfer gate formed by a P-channel MOS transistor 306 and an N-channel MOS transistor 307 is connected between the gates of the transistors 302 and 303, and the ground terminal GND. 
     Also, the transistors 304 and 307 are controlled by an inverted voltage of the input voltage V IN  via an inverter 308, while the transistors 305 and 306 are controlled directly by the input voltage V IN . 
     In accordance with the SCSI standard, when the output voltage V OUT  at the output terminal OUT is 0.5V, the sink current I S  flowing through the transistor 303 is required to be not smaller 48 mA. For realizing this, the gate width W/gate length L of the transistor 303 is 1440 μm/1 μm. In this case, a drain current I 2  of the transistor 303 is calculated by 
     
         I.sub.2 =β.sub.N ·(W/L)·(V.sub.2 -VTHN-V.sub.OUT /2)·V.sub.OUT 
    
     where β N  is a current amplification factor such as 5×10 -5  ; 
     V 2  is a gate-to-source voltage; and 
     VTHN is a threshold voltage such as 0.7V. Also, the transistor 303 is so designed that the voltage V 1  can be increased up to about 4V. For realizing this, for example, the gate width/gate length of the transistor 301 is 36 μm/1 μm, and the gate width/gate length of the transistor 302 is 12 μm/1 μm, In this case, the voltage V 1  is about 3.5V when the output voltage V OUT  is 0.5V. 
     An example of output voltage to drain current characteristics of the transistor 301 is shown in FIG. 8A, and an example of output voltage to drain voltage characteristics of the transistor 301 is shown in FIG. 8B. Note that VTHP is a threshold voltage of the P-channel transistor 301. That is, in a region A where the output voltage V OUT  is relatively high, the drain voltage V 1  is in proportion to the output voltage V OUT . On the other hand, in a region B where the output voltage V OUT  is relatively low, the transistor 301 is in a linear current characteristic region, so that the drain voltage V 1  is in proportion to a square root of the output voltage V OUT . Thus, the drain current I 1  of the transistor 301 represents a transistor square characteristic for the region A, while represents a linear characteristic for the region B. 
     An example of output voltage to drain current characteristics of the transistor 303 is shown in FIG. 9A, and an example of output voltage to drain voltage characteristics of the transistor 303 is shown in FIG. 9B. That is, in the region A where the output voltage V OUT  is relatively high, the drain voltage V 2  is inversely proportional to the output voltage V OUT . On the other hand, in the region B where the output voltage V OUT  is relatively low, the drain voltage V 2  is saturated at a value of V DD  -|VTHP|. Therefore, the drain current I 2  represents a linear characteristic for the region B. 
     When the transfer gate (304, 305) is turned ON and the transfer gate (306, 307) is turned OFF, as shown in FIG. 10, a sink current I S  flowing though the transistor 303 can be represented by a combination of the curve of FIG. 8A and the curve of FIG. 9A. 
     The operation of the output buffer circuit 1-C of FIG. 7 is explained next with reference to FIGS. 11A, 11B and 11C. 
     Note that, before time t 1 , t 3 , . . . , as shown in FIG. 11A, a slightly lower voltage than V DD  determined by the resistors 31 and 32 is applied to the gate of the transistor 301, and therefore, the gate to source voltage of the transistor 301 is not zero. Therefore, a small drain current I 1  flows through the transistor 301. This state corresponds to a state S 1  of FIGS. 10 and 11B. 
     Next, at time t 1 , t 3 , . . . , as shown in FIG. 11A, when the input voltage V IN  at the input terminal IN in changed from 0V to 5V, the transfer gate (304, 305) is turned ON and the transfer gate (306, 307) is turned OFF. As a result, the current mirror circuit formed by the transistors 302 and 303 is activated. Therefore, the drain current I 1  flowing through the transistor 301, i.e., through the transistor 302 is reflected into the drain current I 2  flowing through the transistor 303, which is, in this case, the sink current I S . That is, the sink current I S  is amplified by the amplification factor determined by the transistors 302 and 303. As a result, the output voltage V OUT  is reduced which corresponds to a state S 3  of FIGS. 10 and 11B. 
     When the output voltage V OUT  is reduced, the drain current I 1  flowing through the transistors 301 and 302 is further increased, thus entering a positive feedback control for the sink current I S , which corresponds to a state S 3  of FIGS. 10 and 11B. 
     When the sink current I S  is increased by the positive feedback control up to its maximum value, the output voltage V OUT  is reduced to 0V. 
     Thus, as shown in FIG. 11B, no instataneously large current appears in the sink current I S . As a result, the counter electromotive force due to the sink current I S  determined by the formula (2) becomes small. 
     Therefore, as indicated by Z in FIG. 11C, the ringing phenomenon is suppressed in the output voltage V OUT . 
     On the other hand, at time t 2 , t 4 , . . . , as shown in FIG. 11A, when the input voltage V IN  at the input terminal IN in changed from 5V to 0V, the transfer gate (304, 305) is turned OFF and the transfer gate (306, 307) is turned ON. As a result, the current mirror circuit formed by the transistors 302 and 303 is deactivated. Therefore, as shown in FIG. 11B, the sink current I S  does not flow through the transistor 303. As a result, as shown in FIG. 11C, the output voltage V OUT  becomes a level determined by the resistors 31 and 32. In this case, the ringing phenomenon is small, the same as in FIG. 3C. 
     In FIG. 12, which illustrates a second embodiment of the present invention, a tri-state type output buffer circuit 1-D corresponding to the output buffer circuit 1-B of FIG. 4 is provided. That is, a sink current control portion C1 for controlling the sink current I S  and a drive current control portion C2 for controlling the drive current I D  are provided. 
     The sink current control portion C1 has the same configuration as the output buffer circuit 1-C of FIG. 7, except that the inverter 308 is connected to the transistor 305 and 306. 
     Also, the drive current control portion C2 has a similar configuration to the output buffer circuit 1-C of FIG. 7. 
     The drive current control portion C2 is explained next. An N-channel MOS transistor 601 having a source connected to the ground terminal GND and a gate connected to the output terminal OUT. The transistor 601 converts the output voltage V OUT  into a drain current thereof. 
     A P-channel MOS transistor 602 is connected between the drain of the transistor 601 and the power supply terminal V DD . Also, a P-channel MOS transistor 603 is connected between the output terminal OUT and the power supply terminal V DD . The gate of the transistor 602 is connected to the gate of the transistor 603, and therefore, the transistors 602 and 603 form a current mirror circuit. Also, the size of the transistor 603 is larger than that of the transistor 602, thus enabling a current amplification. Note that the transistor 603 corresponds to the transistor 202 of FIG. 4. 
     In order to control the voltages of the gates of the transistors 602 and 603, a transfer gate formed by a P-channel MOS transistor 604 and an N-channel MOS transistor 605 is connected between the drain of the transistor 601 and the gates of the transistors 602 and 603, and a transfer gate formed by a P-channel MOS transistor 606 and an N-channel MOS transistor 607 is connected between the gates of the transistors 602 and 603, and the power supply terminal V DD . 
     Also, an inverter 408 is connected to the gates of the transistors 405 and 406. 
     Further, two NAND circuits 501 and 502 and an inverter 503 are provided between the terminals EN and IN and the portions C1 and C2. That is, when the enable voltage V EN  at the enable terminal EN is 5V, the transistors 304, 307, 405 and 406 are controlled by an inverted voltage of the input voltage V IN , while the transistors 305, 306, 404 and 407 are controlled by the input voltage V IN . 
     In accordance with the SCSI standard, when the output voltage V OUT  at the output terminal OUT is V DD  -0.5V, the drive current I D  flowing through the transistor 403 is required to be relatively large. For realizing this, the gate width/gate length of the transistor 403 is 360 μm/1 μm. Also, in order to obtain an amplification of the current mirror circuit, the gate width/gate length of the transistor 402 is 12 μm/1 μm. Further, the gate width/gate length of the transistor 401 is 18 μm/1 μm. 
     When the transfer gate (304, 305) is turned ON and the transfer gate (306, 307) is turned OFF, the characteristics of the output voltage V OUT  to the sink current I S  are as shown in FIG. 13A which is the same as FIG. 10. On the other hand, when the transfer gate (404, 405) is turned ON and the transfer gate (406, 407) is turned OFF, the characteristics of the output voltage V OUT  to the drive current I D  are as shown in FIG. 13B. 
     The operation of the output buffer circuit 1-D of FIG. 12 is explained next with reference to FIGS. 14A, 14B, 14C and 13D, Note that the enable voltage V EN  at the enable terminal EN is 5V as shown in FIG. 14A. Also, before time t 1 , t 3 , . . . , as shown in FIG. 14B, a slightly lower voltage than V DD  determined by the resistors 31 and 32 is applied to the gate of the transistor 301, and therefore, the gate to source voltage of the transistor 301 is not zero. Therefore, a small drain current flows through the transistor 301. This state corresponds to a state S 1  of FIGS. 13A and 14C. 
     Next, at time t 1 , t 3 , . . . , as shown in FIG. 14B, when the input voltage V IN  at the input terminal IN is changed from 0V to 5V, the sink current control portion C1 is activated and the drive current control portion C2 is deactivated. 
     That is, the transfer gate (304, 305) is turned ON and the transfer gate (306, 307) is turned OFF. As a result, the current mirror circuit formed by the transistors 302 and 303 is activated. Therefore, the drain current flowing through the transistor 301, i.e., through the transistor 302 is reflected into the sink current I S . That is, the sink current I S  is amplified by the amplification factor determined by the transistors 302 and 303. As a result, the output voltage V OUT  is reduced which corresponds to a state S 2  of FIGS. 13A and 14C. 
     When the output voltage V OUT  is reduced, the drain current flowing through the transistors 301 and 302 is further increased, thus entering a positive feedback control for the sink current I S , which corresponds to a state S 3  of FIGS. 13A and 14C. 
     When the sink current I S  is increased by the positive feedback control up to its maximum value, the output voltage V OUT  reduced to 0V. 
     Thus, as shown in FIG. 14C, no instantaneously large current appears in the sink current I S . As a result, the counter electromotive force due to the sink current I S  determined by the formula (2) becomes small. 
     Therefore, as indicated by Z1 in FIG. 14D, the ringing phenomenon is suppressed in the output voltage V OUT . 
     On the other hand, in the drive current control portion C2, the transfer gate (404, 405) is turned OFF and the transfer gate (406, 407) is turned ON. As a result, the current mirror circuit formed by the transistors 402 and 403 is deactivated. Therefore, the drive current I D  does not flow through the transistor 403. 
     Note that before time t 2 , t 4 , . . . , as shown in FIG. 14B, a slightly higher voltage than 0V determined by the resistors 31 and 32 is applied to the gate of the transistor 401, and therefore, the gate to source voltage of the transistor 401 is not zero. Therefore, a small drain current flows through the transistor 401. This state corresponds to a state S 1  &#39; of FIGS. 13B and 14C. 
     Next, at time t 2 , t 4 , . . . , as shown in FIG. 14B, when the input voltage V IN  at the input terminal IN in changed from 5V to 0V, the drive current control portion C2 is activated and the sink current control portion C1 is deactivated. 
     That is, the transfer gate (404, 405) is turned ON and the transfer gate (406, 407) is turned OFF. As a result, the current mirror circuit formed by the transistors 402 and 403 is activated. Therefore, the drain current flowing through the transistor 401, i.e., through the transistor 402 is reflected into the drive current I D . That is, the drive current I D  is amplified by the amplification factor determined by the transistors 402 and 403. As a result, the output voltage V OUT  is increased which corresponds to a state S 2  &#39; of FIGS. 13B and 14C. 
     When the output voltage V OUT  is increased, the drain current flowing through the transistors 401 and 402 is further increased, thus entering a positive feedback control for the drive current I D , which corresponds to a state S 3  &#39; of FIGS. 13B and 14C. 
     When the drive current I D  is increased by the positive feedback control up to its maximum value, the output voltage V OUT  is increased to V DD  -|VTHP|. 
     When the output voltage V OUT  is further increased, the drain to source voltage of the transistor 403 is remarkably reduced. As a result, the drive current I D  is reduced as the output voltage V OUT  is increased. This corresponds to a state S 4  &#39; of FIGS. 13B and 14C. 
     Thus, as shown in FIG. 14C, no instantaneously large current appears in the drive current I D . As a result, the counter electromotive force due to the drive current I D  determined by the formula (2) becomes small. 
     Therefore, as indicated by Z2 in FIG. 14D, the ringing phenomenon is suppressed in the output voltage V OUT . 
     On the other hand, in the sink current control portion C1, the transfer gate (304, 305) is turned OFF and the transfer gate (306, 307) is turned ON. As a result, the current mirror circuit formed by the transistors 302 and 303 is deactivated. Therefore, the sink current I S  does not flow through the transistor 303. 
     Note that, when the enable voltage V EN  at the enable terminal EN is 0V, the NAND circuits 501 and 502 are deactivated in spite of the input voltage V IN . As a result, in the sink current control portion C1, the transfer gate (306, 307) is turned ON, and the transfer gate (304, 305) is turned OFF, so that the current mirror circuit formed by the transistors 302 and 303 is not operated. Simultaneously, in the sink current control portion C2, the transfer gate (406, 407) is turned ON, and the transfer gate (404, 405) is turned OFF, so that the current mirror circuit formed by the transistors 402 and 403 is not operated. Thus, the output terminal OUT is in a high impedance state, and the output voltage V OUT  is determined by the resistors 31 and 32. 
     As explained hereinabove, since the ringing phenomenon can be suppressed in the output voltage of the output buffer circuit, high speed data transfer for large capacity data can be possible by a SCSI cable.