Abstract:
The present invention relates a frequency multiplier circuit and a controlling method thereof, characterised in that it measures a period of a waveform by a fixed frequency timing signal, and that it reproduces said period by approaching a number of prefixed length subperiods as equal as possible to each other so to minimise the reproduction error thanks to the interpretation of said subperiod number in the following manner m=j * 2′.

Description:
DESCRIPTION  
         [0001]    The present invention relates to a frequency multiplier circuit and a method using above circuit for a period time division in subperiods of length as constant as possible, for a brushless motor.  
           [0002]    A brushless motor is a synchronous motor, the rotation of which is obtained by a current commutation in the windings in a synchronous way with the rotor position. It is necessary, therefore, to know exactly the rotor position to obtain the best accuracy in the motor working, and this position usually is deduced according two approaches: 1) by Hall effect position sensors; 2) by a counter-electromotive force signal (BEMF).  
           [0003]    In this last driving choice the position information is completely stored in the BEMF&#39;s signal, i.e., in the case we have the maximum BEMF we want to impose a maximum torque, in the case we have the zero BEMF we want to impose a zero torque, and when we have a positive and/or negative BEMF we want to impose a positive and/or negative torque and therefore, in order to drive multiphase brushless motors, we have to excite the motor&#39;s phases with voltage waveforms that are shifted 360/n degrees out of phase each other, where n is the number of phase. For example, in a three phase brushless motor, therefore, we have that the voltage waveforms are shifted 360/3=120 degrees out of phase each other and said waveforms are subdivided in a number of samples giving a step waveform able to approximate the driving waveform.  
           [0004]    In FIG. 1 a period time division in subperiods is shown.  
           [0005]    As shown in such figure we note a first axis of abscissa describing a time dependent period signal T c  and a second axis of abscissa describing a time division of said period T c  in subperiods. The T c  signal points out a digital signal having period T c , suitably deduced from BEMF. The difference between period T c  and the subperiods m *  T sys  generates what is commonly known as period reproduction error and in the particular case we have an error E defined by the formula:  
           ε=T c −m * T sys   * INT[INT(T c /T sys )/m] 
           [0006]    with ε in a value range O&lt;ε&lt;m T sys , where INT(num) is a function that rounds a number down to the nearest integer.  
           [0007]    In a steady state, the signal period T c  of the signal is time independent and the error ε committed in the reproduction of period T c  and the reproduced period m * T sys , therefore formed by m subperiods, is a circuit evaluation parameter, that makes the measurement of the period T c.    
           [0008]    Therefore the goodness of the approximation of the motor driving waveform, waveform that changes in function of the connected loads, i.e., the possible range of values among which the error ε can change, is a qualitative and quantitative parameter of the circuit and of the control method thereof.  
           [0009]    In view of the state of the art described, it is an object of the present invention to estimate the period of a particular waveform by a fixed frequency timing signal and to reproduce said period by approaching subperiods as equals as possible each other.  
           [0010]    According to the present invention, such object is achieved by a frequency multiplier circuit comprising an input terminal arranged to receive a period signal, a timing frequency greater than the reverse of said period, a first counter circuit, implemented to execute counting at a fixed first frequency, proportional to said timing frequency, said first counting circuit coupled to a register, a second counter circuit implemented to execute counting at said second timing frequency, characterized in that it comprises an adder node suitable to increase by an unity the content of said register of ADJ subperiods every 2 i  subperiods of said period, where ADJ is the value corresponding to the least significant bit of said register, so that the reproduction error of said period signal is as more little as possible.  
           [0011]    Furthermore, according to the present invention, such object is achieved by a frequency multiplier circuit characterized in that it comprises the following steps: a) accepting a timing frequency greater than of the inverse of said period length; b) executing counting by means of a first counter at first fixed frequency proportional to said timing frequency; c) storing said counting in a register; d) executing counting by means of a second counter circuit at said fixed timing frequency; e) adding by a unity the storing value in said register during the ADJ subdivisions every 2 i  subdivisions of said period; f) comparing an output value of said register and an output value of said second counter; g) generating a second frequency such as to minimise the reproduction error.  
           [0012]    Thanks to the present invention is possible to make a frequency multiplier circuit and a method using above circuit for a period time division, for a brushless motor, able to reproduce the motor driving voltage waveform with an accuracy such to produce a reproduction error as little as possible, making possible to improve the phase relationship between the applied profile and the motor position. 
       
    
    
       [0013]    The features and the advantages of the present invention will be made evident by the following detailed description of an embodiment thereof which is illustrated as not limiting example in the annexed drawings, wherein:  
         [0014]    [0014]FIG. 1 shows a period division in submultiple subperiods;  
         [0015]    [0015]FIG. 2 shows a frequency multiplier circuit for a brushless motor;  
         [0016]    [0016]FIG. 3 shows a frequency multiplier circuit for a brushless motor according to the present invention;  
         [0017]    [0017]FIG. 4 shows a flow chart of an embodiment of a block of the circuit illustrated in FIG. 3;  
         [0018]    [0018]FIG. 5 shows a sketched embodiment of the flow chart illustrated in FIG. 4.  
         [0019]    In the embodiments shown in FIGS. 2, 3,  4   e   5  hereinafter described we refer to circuits particularly for three-phase brushless DC motors for examplary reasons, but the invention is for general purpose circuits adapted for the division of a time variable period into a plurality of subperiods with a reproduction error of the same period as little as possible.  
         [0020]    In FIG. 2 a possible embodiment is shown in the case we want to sample the waveform to be applied to the phases of a three-phase brushless motor (n=3) and to subdivide it into a number m of samples, with m being a multiple of the phase numbers, obtaining a step waveform able to approximate the driving waveform. 
     
    
       [0021]    This kind of embodiment consists in the use of a timing signal at a fixed frequency f c =1/T sys  that is much bigger than the motor electrical frequency f c =1/T c , changing as a function of the working conditions, and to count the period length by using a N bit counter called CP1, timed by a signal obtained by dividing the fixed frequency signal f sys  by the number m of parts in which the motor electrical period T c  is to be subdivided, as shown in FIG. 1. A pin Reset resets the counter CP1, every period T c.    
         [0022]    Once the appropriate counting is obtained, referring to the previous period, the result is stored in a period register RP1 that is refreshed with the value T c , by a pin Latch. The content of said period register RP1 is examined by a comparator CMP1 with a counter timed at frequency f sys . The signals, formed by said CMP1, make a scanning frequency f scan  that is a frequency m−times higher than the indicative signal of the period T c.    
         [0023]    The actual counting in the counter CP1, at every end of the period T c , is defined by the formula p=INT[INT(T c /T sys )/m], and the following period is subdivided by a counter that counts p−times the period T sys  obtaining that every subperiod is, therefore, p * T sys.    
         [0024]    Particularly, if m=36 with n=3, the motor driving consists to apply at the 3 phases three samples shifted by 12 samples out of phase each other, i.e., it is necessary to subdivide the motor electrical period into 36 subperiods as equal as possible to each other.  
         [0025]    In such a case the committed error in the period reproduction changes in function of the period length T c  and of the used frequency to measure f sys  and it is defined by the previous expressed formula:  
         ε=T c −m * T sys   * INT[INT(T c /T sys )/m] 
         [0026]    with ε in a value range O&lt;ε&lt;m T sys.    
         [0027]    In FIG. 3 a frequency multiplier circuit for a brushless motor with greater accuracy is shown.  
         [0028]    If we interpret the number m of parts in which we want to subdivide the period T c  in the following way:  
         m=j *   2   1   
         [0029]    where “i” is the maximum exponent that we can give the factor 2 inside the number m, while j is an odd number also called odd factor.  
         [0030]    As shown in such figure we note that at an input terminal In the circuit receives a period signal T c , measured by a positive-step period counter CP, formed by “N+i” bit, which counting frequency is f cont , counting carried out through the pin Clk; f cont  is j times less than a fixed timing frequency f sys . The frequency f cont  is produced by a block CONT according to prior art.  
         [0031]    The content of the counter CP according to the present invention can be explained as the number of time periods m/T sys  that passed from the start of the current period.  
         [0032]    In fact if we consider for example m=48=3 * 2 4 , that is j=3 and i =4, and considering also T sys =80nsec and T c =1msec we deduce that by making the binary division in function of the circuit signal clock, that is in function of T sys , we have that INT[INT(T c /T sys )/m]=100000100 and the binary division INT[INT(T c /T sys )/j]=1000001000110, and by analyzing this last result unless 4 least significant bits we have the same binary code.  
         [0033]    In fact the least significant “i” bits, also called ADJ, represent an index of the error that we make in the motor driving voltage waveform reproduction.  
         [0034]    The “i” bits stored in the vector ADJ are expressible mathematically by a formula such as:  
         ADJ=INT          r * j −1             
         [0035]    with r=RESTO          INT[INT(T c /T sys )/m]         , where RESTO(num) is a function that returns the division remainder between two numbers, that is the remainder of the division INT[INT(T c /T sys )/m].  
         [0036]    Considering the exemplarily previously given values we obtain the vector ADJ has a decimal form value equal to 6 and transformed into a binary digit formed by 4 bits, we have ADJ=0110; this number corresponds to the least significant 4 bits of the binary division INT[INT(T c /T sys )/j], previously written.  
         [0037]    Therefore what the circuit makes is a division by a number j of a fixed beforehand known frequency f sys , that is f sys /j. This frequency is counted by a counter formed by “N+i” bits. In the most significant N bits of the counter CP there is an outcome equal to the outcome of the frequency counting f sys /m according to the prior art. In the least significant “i” bits of said counter CP there is an error index that we make in the driving voltage waveform reproduction.  
         [0038]    The value stored in CP is evaluated again continuously with the signal T c  by means of a pin Reset, so to form the period T c  that will be output, by means of a pin Out, and stored in a period register RP, having the same dimension as the counter CP, when the new signal T c  arrives, by means of a pin Latch. The register RP is a D type flip-flop storing device.  
         [0039]    A subperiod positive-step counter CSP has a counting frequency equal to the fixed frequency f sys , by the pin Clk, and it is suitable to the subperiod counting, making the time digitalization of the motor driving voltage approximation and it is reset, by the pin Reset, as a fimction of the outgoing value of the logic gate OR, as result of the combination between the signal T c  and a calculated frequency of a comparator circuit CMP, called f scan , where f scan  is a frequency m-times bigger than the signal T c.    
         [0040]    The counter outgoing CSP is the input of the comparator block CMP, by the pin In2, that creates as outgoing signal said frequency f scan  if the value stored in said counter CSP is bigger or equal than the value on the pin In1.  
         [0041]    In order to determine the input value of the comparator CMP a further positive step counter called AC, formed by “i” bits, having a counting frequency equal to f scan , by the pin Clk, is necessary. The counter AC is reset, by the pin Reset, by the signal T c  and it outputs, by the pin Out, the subperiod number present in a period T c.    
         [0042]    Moreover said counter AC starts again to count from 0 after having reached the maximum possible value.  
         [0043]    Moreover a logic gate block AAA has in input, by the pin In1, the “i” bits of the register RP, and it has an outgoing pin Out2 for the only “i” bits representing the vector ADJ, that is the bits representing the error dimension, and it has in input the value stored in the register AC, that is the number associated to the generic subperiod forming the period T c . The block AAA gives as an output, by the pin Out, a true/false value (I/O) depending on a function able to realize any signal clock distribution, i.e., able to add or not a signal clock at every subperiod.  
         [0044]    For example the block AAA can realize a distribution function so that if the stored value of the block AC is less than the value of the vector ADJ the block AAA gives a signal clock to the first ADJ every 2 i  subperiods, with ADJ=INT         r * j −1           .  
         [0045]    In this way the first ADJ every 2 i  subperiods forming the period to be measured are more spaced so to reduce the error ε.  
         [0046]    The outgoing value from said block AAA is added, by an adder node SUM, to the value stored in the most significant bits of the register RP and the value of said sum is the input signal for the comparator CMP. The comparator CMP compares the instantaneous values of the counter CSP with the values given by the sum of what is stored in the most significant bit of the register RP plus the values of the block AAA, therefore the comparator CMP generates the signal f scan  that represents therefore a new reference for the motor rotor position.  
         [0047]    In this way, by adding every 2 i  subperiods a number ADJ of signal clocks, each one having a length of T sys , we obtain a sampling error given by the formula:  
         ε=T c −m * INT[INT(T sys )/m]−j * ADJ * T sys   
         [0048]    with ε in a value range O&lt;ε&lt;j *  T sys , with j *  T sys &lt;m *  T sys    
         [0049]    With the aforementioned values the error in the present invention is in a value range between O&lt;ε&lt;240 nsec, while with the embodiment of FIG. 2 the error is in a value range between O&lt;ε&lt;3480 nsec, that is a range value considerably more reduced.  
         [0050]    We obtain better results, that is a smaller error 6, if the factor 2 has an exponent enough high.  
         [0051]    According to the present invention, therefore, the circuit makes, for example, a distribution of additional signal clocks to the first ADJ subperiods every 2 i  making ε smaller, thereby improving considerably the reproduction precision.  
         [0052]    In a particular embodiment the Applicant has found that we can get a higher distribution uniformity of the additional signal clocks by using the information stored in the vector ADJ, formed by “i” bits, and by the counter value AC, also formed by “i” bits, so to realize a distribution function fit to add signal clocks to the subperiods according a scheme hereinafter described in the flow chart of FIG. 4 and in a schematic simplified circuit representation of FIG. 5.  
         [0053]    In FIG. 4 a flow chart is shown, describing the block implementation AAA of the circuit of FIG. 3.  
         [0054]    As shown in such Figure we note a starting block  1  called START and two allocation blocks  2  and  3 . The block  2  gives the variable ADJBIT a value equal to “i-1” with “i” being the bit number deduced from the formula m=j * 2 i , while the block  3  gives a variable ExClk the boolean value FALSE. The variable ExClk, at the end of the analyzing process of every bits, is explainable as the outgoing signal, by the pin Out, from the logic gate block AAA shown in FIG. 3 or also as the circuit outgoing shown in FIG. 5.  
         [0055]    Afterwards a test  4  is performed to verify if the vector value ADJ in position ADJBIT is equal to 1, that is if the bit in given position ADJBIT is one or is a zero. In the affirmative case, path  5 , the assignment “i-1-ADJBIT”, block  6 , to a variable ADJCntLim is performed.  
         [0056]    Moreover two assignment blocks  7 , wherein an index j is set to zero, and 8, wherein a temp variable Serv is set to a boolean value TRUE, are performed in succession.  
         [0057]    Moreover a further test  9  is performed to verify if the index value j is less than the variable value ADJCntLim. In the affirmative case, path  10 , an AND operation between the variable Serv and the counter value AC in position j is performed, that is the variable Serv is equal to 1 if the bit in position “j” of the counter AC is 0.  
         [0058]    A unit increment operation of the index j, block  12 , is then performed and moreover, path  26 , a further test cycle  9  is performed. In the case the test  9  is negative, path  21 , that is in the occurrence that the index j is greater than the variable value ADJCntLim, a block  13  is performed wherein an operation AND is performed between a boolean value (true/false) and the result of condition AC(j)=0, that is we have that the variable Serv is equal to 1 if the bit in the position “j” of the counter is 1.  
         [0059]    Afterwards an assignment block  14  is performed, wherein an operation OR is performed between the variables ExClk and Serv, that is we decide if we give an additional signal clock or not, outputting from the block AAA of FIG. 3 a high value, that is 1.  
         [0060]    Moreover an assignment block  15  is performed, wherein we decrease by a unit the variable value ADJBIT and subsequently a test  16  is performed on said variable ADJBIT. If the result is positive, path  17 , the test  4  is processed again, while if the result is negative, path  18 , the flow chart ends.  
         [0061]    The block  15  is performed immediately after the test  4  in the case of the test result is negative, path  20 , that is the case of the vector ADJ in position ADJBIT is different from 1.  
         [0062]    It is possible to obtain a signal clock complementary distribution having analogous properties by changing in the assignment blocks  11  e  13  the condition to which AC(j) must to be submitted, that is AC(j)=1 in the block  11  and AC(j)=0 in the block  13 .  
         [0063]    The block AAA has, therefore, as input the counter AC and the vector bit ADJ and it gives as output a value true/false (I/O), that is the variable ExClk, according to a circuit, described in a schematic way in FIG. 5, according to the most significant bit of the “i” bits.  
         [0064]    In fact the flow chart of FIG. 4 according to the most significant bit of the “i” bits of the vector ADJ, vector symbolizing the reference and therefore is constant during the whole period T c , and according to the counter value AC, that changes at every subperiod, uses the most significant bit of ADJ, that is the necessity to add a signal clock to the half of subperiods, choosing indifferently the even subperiods of AC (least significant bit equal to 0) or the odd subperiods of AC (least significant bit equal to 1). The second most significant bit of the “i” bits is the necessity to add a signal clock to a quarter of subperiods of AC, choosing indifferently among previously not observed even (least significant bit 0 and second least significant bit 1) or odd subperiods (least significant bit 1 and second least significant bit 0). We can iterate this method for all the bits of the counter AC.  
         [0065]    For example, in the first cycle of the flow chart, being AC an “i” bits counter that counts the subperiods from zero from the period start and that starts again from zero every time the saturation is reached, if the most significant bit of ADJ is equal “1”, it means that at least a half of the subperiods must be the additional signal clock and therefore we can add at every odd subperiod a signal clock, that it can be distinguished by the fact that the least significant bit of the counter AC is equal to 1.  
         [0066]    At the second cycle of the flow chart if the second least significant bit of ADJ is equal “1” it means that al least a quarter of the subperiods must have the additional signal clock and therefore we can add the signal clock to the even subperiods (that aren&#39;t called in the previous cycle) that aren&#39;t multiple of 2 2 ; these subperiods are distinguished by the following features: in the counter AC the least significant bit is equal “0”, while the second least significant bit is equal “1”.  
         [0067]    At the third cycle of the flow chart if the third least significant bit of ADJ is equal “1” it means that al least one eighth of the subperiods must be the additional signal clock and therefore we can add the signal clock to the even subperiods that are multiple of 2 2  (that aren&#39;t called in the previous cycle) but aren&#39;t multiple of 2 3 ; these subperiods are distinguished by the following features: in the counter AC the least significant bit is “0”, the second least significant bit is “0”, while the third least significant bit is “1”.  
         [0068]    This process can be iterated for all the “i” bits of the counter AC and in the vector ADJ, to the end of the bits.  
         [0069]    In FIG. 5 a schematic embodiment of the flow chart of FIG. 4 is shown.  
         [0070]    As shown in such figure we note a plurality “i” of gate logic AND  22 ,  23  e  24 , wherein “i” is an index deduced by the formula m=j * 2 i , and their outgoing signal is the input of a OR logic gate  25 . The logic gate  22 , for example, outputs a value that is high only if the inputs are high, that is in the case that the vector value ADJ, in position “i-1”, that is the most significant bit, and the counter value AC, in position zero, that is the least significant bit, are equal to 1. That is the most significant bit of the vector ADJ is equal to 1 and the least significant bit of the counter AC is equal to 1 and therefore, for example, at least the half of the subperiods must be a signal clock and we can add this signal clock at every odd subperiod by outputting an high value from the logic gate  25 . Analogous argument worthies for the logic gates  23  e  24 .