Abstract:
Disclosed herein is a method and system to reduce the area and power dissipation in digital filters or multipliers. Compared to radix-4 Booth coding the proposed method reduces the number of partial products by one, if the input signal has certain limits on its range. One exemplary application is echo cancellation in a fill duplex pulse amplitude modulation system with 10 levels (PAM-10). Echo cancellation may be achieved by calculating a digital replica of the echo from the transmission channel. The replica signal may be calculated in a finite impulse response (FIR) filter, which multiplies the transmitted signal with estimates of the echo coefficients of the transmission channel. The replica signal may be subtracted from the received signal to create an echo-free receive signal. The disclosed method may reduce the number of partial products between the PAM-10 transmit signal and each echo coefficient from three, when radix-4 Booth coding is used, to two. This in turn may reduce the number of adders in each tap multiplier of the FIR filter from two to one, resulting in lower area, lower power dissipation, and potentially higher switching speeds.

Description:
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   BACKGROUND OF THE INVENTION 
   Information transmission at maximum transmission rates is the quest of the information transmission designer. Adapting existing data transmission infrastructure to accommodate faster transmission rates may also be desirable. As data transmission rates are increased, data corruption may result from effects such as attenuation, echo, return loss, and crosstalk in the existing transmission infrastructure. 
   Attenuation may be defined as signal loss between a transceiver and a receiver. Attenuation may increase with increasing data transmission frequency. Echo may occur as a result of full duplex operation or parallel transmission, i.e., where both the transmit and receive signals are active on the same wire. Residual transmit signal and cabling return loss may combine to produce unwanted signals which may be referred to as echo. Echo may occur due to power reflections due to cable impedance mismatches. 
   Further limitations and disadvantages of conventional and traditional approaches will become apparent to one of skill in the art, through comparison of such systems with embodiments presented in the remainder of the present application with reference to the drawings. 
   SUMMARY OF THE INVENTION 
   Aspects of the present invention may be found in a method of operating a signal processing device. The method may comprise receiving a signal sample; encoding the signal sample using a coding process to produce symbolic values; modifying the symbolic values to reduce a number of digits used to represent the symbolic values and produce coded values; and processing the coded values in the signal processing device. 
   In an embodiment of the present invention, the coding process may be a radix-4 Booth coding process. 
   In an embodiment of the present invention, modifying the symbolic values may comprise changing a value of a digit in the coding process based upon a value in a next higher order digit of the symbolic value to create the coded value. 
   In an embodiment of the present invention, processing may comprise using the coded values input to the signal processing device. The signal processing device may comprise a digital filter. 
   In an embodiment of the present invention, the digital filter may comprise a finite impulse response filter. 
   In an embodiment of the present invention, processing the coded values in the signal processing device may further comprise inputting the coded values to the signal processing device; directing the coded values to a plurality of multipliers; multiplying the coded values by coefficients forming a plurality of products; directing the products to a plurality of adders; summing the products to produce a processed signal; delaying output of the processed signal by at least one unit delay; and outputting the processed signal. 
   In an embodiment of the present invention, multiplying the coded values by coefficients forming a plurality of products may further comprise directing the coded values to a plurality of multipliers and a plurality of sign inverters; multiplying the coded values by first coefficients in the multipliers to form at least one first product; and multiplying the coded values by at least one second coefficient in the sign inverters to form at least one second product. 
   Aspects of the present invention may also be found in a method of increasing a bit rate of transmission of a signal. The method may comprise receiving a signal sample; encoding the signal sample using a coding process to produce symbolic values having a particular number of bits; modifying the symbolic values to reduce a number of digits used to represent the symbolic values and produce coded values; and processing the coded values in the signal processing device. 
   In an embodiment of the present invention, reducing the number of digits used to represent the symbolic values may further comprise eliminating at least one digit during the coding process without losing any digital information; and processing more digital information per unit time with fewer processing operations. 
   In an embodiment of the present invention, the coding process may be a radix-4 Booth coding process. 
   In an embodiment of the present invention, modifying the symbolic values may comprise changing a value of a digit in the coding process based upon a value in a next higher order digit of the symbolic values to create the coded values. 
   In an embodiment of the present invention, processing may comprise using the coded values input to the signal processing device. The signal processing device may comprise a digital filter. 
   In an embodiment of the present invention, the digital filter may comprise a finite impulse response filter. 
   In an embodiment of the present invention, processing the coded values in the signal processing device may further comprise inputting the coded values to the signal processing device; directing the coded values to a plurality of multipliers; multiplying the coded values by coefficients forming a plurality of products; directing the products to a plurality of adders; summing the products to produce a processed signal; delaying output of the processed signal by a at least one unit delay; and outputting the processed signal. 
   In an embodiment of the present invention, multiplying the coded values by coefficients forming a plurality of products may further comprise directing the coded values to a plurality of multipliers and a plurality of sign inverters; multiplying the coded values by first coefficients in the multipliers to form at least one first product; and multiplying the coded values by at least one second coefficient in the sign inverters to form at least one second product. 
   Aspects of the present invention may also be found in a signal processing device comprising an input adapted to receiving a signal sample; an encoder adapted to encoding the signal sample using a coding process to produce symbolic values; and a processor adapted to modify the symbolic values to reduce a number of digits used to represent the symbolic values, produce coded values, and process the coded values in the signal processing device. 
   In an embodiment of the present invention, the device may further comprise a plurality of multipliers; and a plurality of adders, wherein coded values may be input to the signal processing device, multiplied by a plurality of coefficient bits in the plurality of multipliers to create a plurality products, wherein the products may be summed together, and the processed signal may undergo a unit delay before being output from the signal processing device. 
   In an embodiment of the present invention, one coding process that the encoder may be adapted to perform is a radix-4 Booth coding process. 
   In an embodiment of the present invention, in modifying the symbolic values, the processor may be adapted to change a value of a digit in the coding process based upon a value in a next higher order digit of the symbolic values to create the coded value. 
   In an embodiment of the present invention, the signal processing device may comprise a digital filter. 
   In an embodiment of the present invention, the digital filter may comprise a finite impulse response filter. 
   In an embodiment of the present invention, the signal processing device may also be adapted to input the coded values; multiply the coded values by coefficient bits forming a plurality of products; sum the products to produce a processed signal; delay output of the processed signal by a at least one unit delay; and output the processed signal. 
   In an embodiment of the present invention, the signal processing device may also be adapted to multiply the coded values by first coefficients in the multipliers to form at least one first product; and multiply the coded values by at least one second coefficient in sign inverters to form at least one second product. 
   These and other advantages and novel features of the present invention, as well as details of an illustrated embodiment thereof, will be more fully understood from the following description and drawings. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
       FIG. 1  is a diagram illustrating a multiplier according to an embodiment of the present invention; 
       FIG. 2  illustrates a finite impulse response filter with a 10-level input signal according to an embodiment of the present invention; and 
       FIG. 3  is a flow chart illustrating processing of signals using a finite impulse response filter with a 10-level input signal according to an embodiment of the present invention. 
   

   DETAILED DESCRIPTION OF THE INVENTION 
   Information bits may be serially transmitted using at least two level symbols, and there may be a one-to-one correspondence between the bits and the symbols. The one-to-one correspondence between the bits and symbols may result in a signal with significant frequency components at the bit rate frequency. 
   Communication channels may experience significant integrity degradation at higher frequencies. In some cases, communication channels may provide high quality up to a certain threshold frequency. However, at frequencies above the threshold frequency, the degradation may be very sharp, rendering communications beyond the threshold frequency impossible without providing error correction to the signals. 
   Many existing transmission infrastructures are provided with Category 5 (Cat-5) cabling solutions. Cat-5 cables are defined as comprising four unshielded twisted pairs of wires in a single jacket. In many networks, a Cat-5 cable may connect a transceiver and a receiver to provide 4 times parallel data transmission capabilities. In these systems, all four twisted pairs of wires in the Cat-5 cable may be employed simultaneously to provide four times the data transmission capability of a single cable having a pair of wires. 
   Communication channels having a threshold frequency may limit the data transmission rate to the threshold frequency. To overcome these shortcomings, the Pulse Amplitude Modulation level 5 (PAM-5) standard was developed for coding data words. 
   The PAM-5 standard may be employed to encode 8-bit data words with four five-level symbols. A number of encoders may operate in unison to achieve a high data transmission throughput rate. The symbols generated by each of the encoders may be transmitted in parallel with respect to one another. 
   Parallel transmission may be incompatible with some preexisting networks designed for serial transmissions. An embodiment according to the present invention may comprise a method of data coding to adapt a transmission infrastructure to higher speed data transmission. 
   PAM-5 is adapted to provide greater bandwidth than binary signaling. In binary signaling, each transmitted symbol represents one bit, for example, 0 or 1. In PAM-5, each transmitted symbol represents one of five different levels, for example, (−2, −1, 0, 1, 2). Because each symbol can represent two bits of information, (four levels to represent two bits, plus an extra fifth level which may be used for error correction coding), the symbol rate, and therefore also the signal bandwidth, may be reduced by a factor of two. The fifth level of coding may provide error correction to recover transmitted symbols in the presence of signal interference such as, echo, crosstalk, etc. 
   Signal equalization may also be used to compensate for signal distortion introduced by the communication channel. Linear digital equalization may be provided by a finite impulse response (FIR) filter. For PAM-5, a five level FIR filter may be employed. 
   In order to increase data transmission rates, that is, in order to send more data over the same data channels per unit time, it may be necessary to transmit more symbols in the same amount of time or transmit more bits per symbol. In an embodiment according to the present invention, PAM-10, i.e., 10 level pulse amplitude modulation, may be employed to increase the rate of data transmission, i.e., the bit rate, by transmitting more bits per symbol. 
   PAM-10 is adapted to provide greater bandwidth than PAM-5 and binary signaling. In PAM-10, each transmitted symbol represents one of ten different levels, for example, (−9, −7, −5, −3, −1, 1, 3, 5, 7, 9). For signal processing reasons, each symbol may represent four bits of information. Because each symbol can represent four bits of information, the symbol rate, and therefore also the signal bandwidth, may be reduced. 
   Signal equalization may also be used to compensate for signal distortion introduce by the communication channel. Linear digital equalization may be provided by a finite impulse response (FIR) filter. FIR filters provide echo cancellation by performing multiplications of the input signal by selected coefficients. These multiplications may produce a large number of products and additions, which may consume filter chip area and power, produce processing delays that limit symbol rate, and cause other data transmission delays. 
   Cables used for signal transmission have limited bandwidth capabilities. In order to move information at higher bit rates, more bits per symbol may be encoded. Building an echo cancellation device using a greater number of bits per symbol, ordinarily would increase the delay, chip real estate, power consumption, etc. for the echo cancellation device. 
   In an embodiment according to the present invention, Booth coding may be applied to multiply the input samples by interference cancellation coefficients. Booth coding may provide a reduction in the complexity of multiplication circuits by recoding the numbers being multiplied in a more compact form. 
   One approach to perform multiplication is to shift and add, i.e., long multiplication. For each column in the multiplier, the multiplicand is shifted the appropriate number of columns, and multiplied by the value of the digit in that column of the multiplier to obtain a product. 
   Following the conventional method of long multiplication, the number of products is exactly the number of columns in the multiplier. It may-be possible to reduce the number of products by half using a technique of radix-4 Booth coding, or modified Booth coding. Using radix-4 Booth coding, instead of shifting and adding for every column of the multiplier term and multiplying by 1 or 0, it is possible to take two columns at a time, and multiply by 2, 1, 0, −1 or −2, to obtain the same result. Therefore, to multiply by 7, for example, we can multiply the product aligned against the least significant bit (LSB, first column) by −1, and multiply the product aligned with the third column by 2, for example:
         Product 0=Multiplicand*−1, shifted left 0 bits;   Product 1=Multiplicand*2, shifted left 2 bits.       

   This gives the same result as the equivalent shift and add long multiplication method, shown below, but using fewer multiplication operations.
         Product 0=Multiplicand*1, shifted left 0 bits;   Product 1=Multiplicand*1, shifted left 1 bit;   Product 2=Multiplicand*1, shifted left 2 bits;   Product 3=Multiplicand*0, shifted left 3 bits.       

   An advantage of this method is the halving of the number of products, resulting in a decrease in propagation delay in data transmission, reduction in the complexity of the circuit, and reduction in the power consumption of the circuit, and the ability to more compactly code information. 
   To Booth code the multiplier term, note that the bits of a block overlap adjacent blocks by one bit. Grouping starts with the LSB, and the first block only uses two bits of the multiplier because there is no previous block to overlap. 
     FIG. 1  is a diagram illustrating a multiplier  111  according to an embodiment of the present invention. In  FIG. 1 , a set of control signals may be applied to the multiplier  111 . The values of each of the control signals causes the multiplier  111  to operate upon an incoming coded value, as discussed below, in a particular manner, (i.e., zero, negate, multiply/shift by one or two columns). Three digital control signal inputs ( 888   a ,  888   b , and  888   c ) may be provided, wherein at each control signal input, either a 1 or 0 may be input. 
   The three digital control signals together cooperatively determine the particular multiplication operation that is performed upon the coded input. The particular operation that the multiplier  111  performs upon the coded input signal may vary, based upon the relationship of the three control signal inputs ( 888   a ,  888   b , and  888   c ) operating together as discussed below. 
   Coded input values may be multiplied by a plurality of coefficient bits ( 444   a ,  444   b , and  444   c ), which may be input to a plurality of selectors  777 , and a plurality of exclusive or (XOR) gates  666 , and a plurality of AND gates  555 , to modify the coded values, and thus modify the corresponding transmitted signal. 
   In an embodiment according to the present invention, the output of the Booth coder with the input being bits from the multiplier may be as follows:
         Bits from multiplier→[Booth Coder]→Negate   Bits from multiplier→[Booth Coder]→Zero   Bits from multiplier→[Booth Coder]→shift (x 1  or x 2 ).       

   The zero signal may indicate whether the multiplicand is zeroed before being used as a product, which may be the same as multiplying by 0. The shift signal (x 1  or x 2 ) may be used as a control signal to a 2:1 multiplexer to select whether or not the product bits are shifted left zero or one position, which may be the same as multiplying by 1 or 2. The negate signal may indicate whether or not to invert (sign inversion) all of the bits to create a negative product, which may be the same as multiplying by −1. 
   
     
       
             
           
             
             
             
             
             
           
         
             
               TABLE 1 
             
           
           
             
                 
             
             
               Multiplier Operations and Control Signal Inputs 
             
           
        
         
             
                 
               Input 1 
                 
                 
                 
             
             
                 
               (888c) 
             
             
                 
               (Multiply by 
               Input 2 (888b) 
               Input 3 (888a) 
               Output 
             
             
               Row 
               1 or 2) 
               (Negate) 
               (Zero) 
               (Results) 
             
             
                 
             
             
               1 
                X 
                  X 
                       0 
                0*Multiplicand 
             
             
               2 
               0 
               0 
               1 
               1*Multiplicand 
             
             
               3 
               1 
               0 
               1 
               2*Multiplicand 
             
             
               4 
               0 
               1 
               1 
               −1*Multiplicand   
             
             
               5 
               1 
               1 
               1 
               −2*Multiplicand   
             
             
                 
             
           
        
       
     
       
       
         
           Table 1 illustrates possible multiplication operations which may be performed by a multiplier according to an embodiment of the present invention. 
         
       
     
  
   According to an embodiment of the present invention, and illustrated in Table 1 above, row 1 reveals a situation wherein regardless of what the input control signal values are at input  1   888   c  and input  2   888   b , (represented by X), when the input control signal value at input  3   888   a  is 0, then the outputs, ( 333   a ,  333   b ,  333   c , and  333   d , etc., for example), are 0, (i.e., being the same as multiplying the coded value by zero, 0*Multiplicand). Alternatively, when the input value at input  3   888   a  is 1, then the coded value is passed through unchanged, (being the same as multiplying by 1). 
   In row 2, when input  1   888   c  and input  2   888   b  are both 0, (i.e., meaning the coded value is passed through unchanged), then the outputs ( 333   a - 333   d ) are 1*Multiplicand. Of course, input  3   888   a  must be 1, otherwise the outputs ( 333   a - 333   d ) are 0. 
   In row 3, when input  1   888   c  is 1 and input  2   888   b  is 0, then the outputs ( 333   a - 333   d ) are 2*Multiplicand. This demonstrates that the corresponding operation of input  1   888   c  is to pass the coded value through unchanged when input  1   888   c  is 0, (i.e., passing through unchanged being the same as multiplying by 1), and shifting the coded value 1 column or position when input  2   888   b  is 1, (i.e., being the same as multiplying the coded value by 2). Of course, input  3   888   a  must be 1, otherwise the outputs ( 333   a - 333   d ) are 0. 
   In row 4, when input  1888   c  is 0 and input  2   888   b  is 1, then the outputs ( 333   a - 333   d ) are −1*Multiplicand. This demonstrates that the corresponding operations on a coded value by when input  2   888   b  is 1 is a sign inverting process, (i.e., being the same as multiplying by a −1), and when input  2   888   b  is 0, the coded value is passed through unchanged, (i.e., being the same as multiplying by 1). Of course, input  3   888   a  must be 1, otherwise the outputs ( 333   a - 333   d ) are 0. 
   In row 5, when input  1888   c  is 1 and input  2   888   b  is 1, then the outputs ( 333   a - 333   d ) are −2*Multiplicand. Of course, input  3   888   a  must be 1, otherwise the outputs ( 333   a - 333   d ) are 0. 
   In an embodiment according to the present invention, the method may comprise further reducing the number of digits required to code a particular number or value. In an embodiment according to the present invention, the method may comprise reducing the coded value by at least one digit, (i.e., eliminating at least one digit in the coding process), resulting in fewer digits being necessary to be transmitted, while transmitting the same amount of data per unit time. 
   For example, 5 bits may be required to transmit the numerical value of negative nine. However, by recognizing that −9=−16+8−1 or alternatively, −9=(−2*4)−1, the coding for the value may be significantly reduced, at least reduced by one digit, for example. 
   For an n-bit word, up to n operations are required to perform the multiplications using standard Booth coding. However, according to an embodiment of the present invention, using a modified Radix-4 Booth coding scheme, for an n-bit word, fewer operations are required to perform the multiplications. 
   The operations performed may be additions, subtractions, or no operations at all, for every two bits of the original data word. According to an embodiment of the present invention, because half of the multiplication operations have been eliminated, therefore the logic is required to code the values over the standard binary multiplication method. 
   In an embodiment according to the present invention, a method of optimized coding of a pulse amplitude modulated level 10 (PAM-10) signal may be performed as follows. In PAM-10, there are 10 levels represented by the values in the following table. 
   
     
       
             
           
             
             
             
             
           
             
             
             
             
             
             
             
           
             
             
             
             
             
             
             
           
         
             
               TABLE 2 
             
           
           
             
                 
             
             
               Comparison of Various Coding Values 
             
           
        
         
             
                 
                   Booth Coded 
                     Optimum Coded 
                 
             
           
        
         
             
                 
                 
                16 
               4 
                1 
                4 
                  1 
             
             
               Decimal 
               Binary 
               x b   4   
               x b   2   
               x b   0   
               x o   2   
               x o   0   
             
             
                 
             
           
        
         
             
                    −9 
                  10111 
               −1 
               +2 
               −1 
               −2 
                −1 
             
             
               −7 
               11001 
               0 
               −2 
               +1 
               −2 
               +1 
             
             
               −5 
               11011 
               0 
               −1 
               −1 
               −1 
               −1 
             
             
               −3 
               11101 
               0 
               −1 
               +1 
               −1 
               +1 
             
             
               −1 
               11111 
               0 
               0 
               −1 
               0 
               −1 
             
             
               1 
               00001 
               0 
               0 
               +1 
               0 
               +1 
             
             
               3 
               00011 
               0 
               +1 
               −1 
               +1 
               −1 
             
             
               5 
               00101 
               0 
               +1 
               +1 
               +1 
               +1 
             
             
               7 
               00111 
               0 
               +2 
               −1 
               +2 
               −1 
             
             
               9 
               01001 
               +1 
               −2 
               +1 
               +2 
               +1 
             
             
                 
             
           
        
       
     
       
       
         
           Table 2 illustrates a comparison of a plurality of coded values according to an embodiment of the present invention. 
         
       
     
  
   Applying the optimum coding scheme according to the present invention, (modified radix-4 Booth coding), only two digits may be used to code and represent symbolic values that would ordinarily require three digits to code or represent applying previous coding techniques. Therefore, according to an embodiment of the present invention, 10 levels may be encoded employing 4 bits (i.e., 2 radix−4 digits). 
   The radix-4 Booth code may be defined as follows:
 
 C*X=C*X   b   0 +4 *C*X   b   2 +16 *C*X   b   4  
         wherein two adders are required to calculate the product C*X, and 6 bits are needed to represent X b .       

   The optimum code according to the present invention may be defined as follows:
 
 C*X=C*X   O   0 +4 *C*X   O   2  
         wherein only one adder may be used to calculate C*X, and no hardware may be required to calculate 16*C*X b   4 , and only four bits may be required to represent X O . It is noted that only two values of the radix 4 Booth coding used to express the X b   4  digit of the PAM-10 signal are non-zero (i.e., 9 and −9, as shown above).       

   In an embodiment of the present invention, by changing the sign of the radix 4 Booth coded digit corresponding to X b   2  (i.e., from + to −, and from + to −) for the encoding of −9 and +9, the digit corresponding to X b   4  may be eliminated. This result is possible because only a portion of the range of values, (i.e., −9 and +9), of X b   4  digit of a 3 digit Booth coded value are needed. 
   Therefore, according to an embodiment of the present invention, because the multiplication operation has been simplified by the reduction of a term, (i.e., the X b   4  term having been eliminated), the processing hardware may be simplified, the power consumption is reduced, and the circuit chip area used for the processing is reduced. Although the present invention has been described herein with respect to embodiments utilizing digital filters, and in particular, finite impulse response filters, an embodiment according to the present invention may have application in other systems involving the processing of digital information in which only a portion of the range of coded digital values is used. 
   In an embodiment of the present invention, the method comprising application of optimum coding as set forth above may provide at least one less adder for every multiplier and eliminate at least one partial product multiplier for the operation [−1, 0, 1]*C resulting in faster data transmission than previous data transmission applications. 
   Further according to an embodiment of the present invention, the optimum coding scheme may be distributed with two bits less than previous data transmission application resulting in at least area reduction, i.e., integrated circuit area reductions, and power savings over previous data transmission applications. 
   According to an embodiment of the present invention, the optimum coding scheme may also be applicable to systems employing an even greater number of pulse amplitude modulation levels, for example, PAM-21, and PAM-40, when a restricted range of levels is used. The number of Booth coded digits may be reduced through coding according to an embodiment of the present invention. For example, by coding the following values [−10, −9, −8, . . . 8, 9, 10] a 21 level coding scheme (PAM-21) may be realized. 
   In an embodiment of the present invention, application of the optimum coding method may be performed when X b   n  and the most significant digit in a modified Booth coded number uses values between [+1, 0, −1] and if the following condition hold true:
         1) when X b   n =−1, then X b   n−2 =2; and   2) when X b   n =1, then X b   n−2 =−2.       

     FIG. 2  illustrates a finite impulse response (FIR) filter  100  with a 10-level input signal according to an embodiment of the present invention. In  FIG. 2 , the input  110  to FIR filter  100  may be a 10-level input signal as explained above and may be designated by the value X. Encoding the signal sample may be performed by an encoder (not shown) using a coding process to produce symbolic values. 
   A 10-level input signal may comprise, for example, values as follows:
         X=−9, −7, −5, −3, −1, 1, 3, 5, 7, 9.       

   The signal value X enters the FIR filter  100  at input  110 . The input signal, having one of the 10 values above is passed through a plurality of multipliers  120  where the signal is multiplied by coefficients, for example C 0 , C 1 , C 2 , . . . , C n  creating a plurality of products. The products may then be directed to a plurality of adders  130 . The outputs of each of the adders  130  may be delayed for a time represented by unit delay  150  before being passed to the next adder  130  and eventually to output  190 . 
   Accordingly, after processing, Y may be described as a function of X, where k may be defined as a unit of time, as shown below:
 
 Y ( k ) =C   0   *X ( k− 1)+ C   1   *X ( k− 2)+ C   2   *X ( k− 3)+ . . .  C   n   *X ( k−n+ 1). 
 
   According to an embodiment of the present invention, signal processing for a input signal X=[X 0 , X 1 , X 2 , . . . ] may be defined as follows: 
             Time   _             Output   ⁢           ⁢   Signal     _               k   =   0         0             k   =   1             X   0     *     C   0                 k   =   2               X   1     *     C   0       +       X   0     *     C   1                   k   =   3               X   2     *     C   0       +       X   1     *     C   1       +       X   0     *     C   2                   k   =   4               X   3     *     C   0       +       X   2     *     C   1       +       X   1     *     C   2       +       X   0     *     C   3                 …       …             k   =   n               X     n   -   1       *     C   0       +       X     n   -   2       *     C   1       +       X     n   -   3       *     C   2       +       X     n   -   4       *     C   3       +   …   +       X     n   -   m       *     C     m   -   1                   
         where k is a quantity of time, X is a 10 level coded input signal, and C j , j=0 . . . m are the coefficients.       

   The multipliers may perform at least one of the operations discussed above on the values of the control signals controlling the multipliers. After the ation operations are performed the coded values may be directed to the plurality of adders  130 . The products may be summed and the output may be delayed by at least one unit delay  150 . The signal may then be output  190  from the filter. The input signal  110 , after multiplications, additions, etc., makes up the output signal  190  from the filter  100 . 
     FIG. 3  is a flow chart  300  illustrating processing of signals using a finite impulse response filter with a 10-level input signal according to an embodiment of the present invention. In  FIG. 3 , initially an analog signal may be received (block  310 ). The analog signal may be converted to a digital signal using an A/D converter (block  320 ). The signal may then be encoded using a modified Booth coding procedure (block  330 ), as discussed above. The coded signal may be input to a signal processing system (block  340 ) which may comprise a FIR filter for signal processing (block  350 ). 
   During signal processing in the FIR filter of the signal processing system, the coded signal values may be passed to multipliers where they may be multiplied by coefficients. Products resulting from the multiplications may be directed to adders. The products may be summed. The processed signal may be delayed by at least one unit delay. The signal may then be output (block  366 ) from the signal processing system. 
   Processing signals according to the embodiment illustrated in  FIG. 3 , enables the complexity of signal processing systems to be reduced by simplifying the complexity of multiplication circuits. An advantageous result according to an embodiment of the present invention is decreasing processor chip size and therefore processor cost by processing more information with coded values comprising more information or bits per symbol. 
   The signal processing method according to the present invention may avoid interference and signal distortion because the information is transmitted without increasing the frequency of operation to intolerable levels. Signal processing activity is also reduced by recoding the signal values being processed in a more compact form thus permitting an increased throughput, or more bits per symbol being transmitted per unit time. Power consumption may also be reduced because less processing is required to transmit more information with fewer coded values according to an embodiment of the present invention. 
   In an embodiment according to the present invention, modified Radix-4 Booth coding permits using only 4 digits for the encoding of a PAM-10 signal, resulting in at least a halving of the number of products to be processed. In an embodiment according to the present invention, the filter chip size may be reduced while at the same time providing a higher bit rate of transmission. The delay in transmission may also be reduced resulting in faster transmission. Additionally the amount of power consumed per operation may also be decreased. 
   In an embodiment according to the present invention, a 2.5 Gigabit/second data transmission rate may be accomplished by applying the PAM-10 coding method and a standard Cat-5 cables. Remembering that a Cat-5 cable comprises 4 unshielded twisted wire pairs, and by transmitting 3 bits per symbol at a frequency of 208 MHz, the 2.5 Gigabit/second transmission rate may be described as follows:
         (4 wire pairs)*(208 MHz transmission frequency)*(3 bits per symbol) is approximately 2.5 Gigabits of information transmitted per second.       

   In an embodiment of the present invention, more information, i.e., a greater number of bits may be transmitted in the same amount of time using PAM-10 coding techniques. Although PAM-10 coding has been described in the present application, PAM-21, PAM-40, etc., may also be applied where appropriate to further increase the bit rate of data transmission by increasing the number of bits per symbol being coded. The invention may also be used in multipliers. 
   The foregoing description of the exemplary embodiment of the invention has been presented for the purposes of illustration and description. It is not intended to be exhaustive or to limit the invention to the precise form disclosed. Many modifications and variations are possible in light of the above teaching. It is intended that the scope of the invention be limited not with this detailed description, but rather by the claims appended hereto. 
   While the invention has been described with reference to certain embodiments, it will be understood by those skilled in the art that various changes may be made and equivalents may be substituted without departing from the scope of the invention. In addition, many modifications may be made to adapt a particular situation or material to the teachings of the invention without departing from its scope. Therefore, it is intended that the invention not be limited to the particular embodiment disclosed, but that the invention will include all embodiments falling within the scope of the appended claims.