Abstract:
A system and method of digitizing an analog signal without an amplitude channel is disclosed. The system and method includes receiving an analog signal comprising a voltage v(t) and a frequency f1, producing a series of optical pulses at a sampling frequency f2 with a pulsed laser, splitting the series of optical pulses into a first optical signal and an optical reference signal, phase modulating the first optical signal with the analog signal to produce a sampled optical signal such that phase shifts between adjacent samples in the sampled optical signal does not exceed π radians, and receiving the sampled optical signal and the optical reference signal at a photonic signal processor.

Description:
FIELD OF THE INVENTION 
     The present specification relates to improving the performance of optically interleaved electronic analog-to-digital converters (ADC) implemented in various communications systems including radio-frequency (RF) communication systems. 
     Military RF system designers have long been aware that wide bandwidth, high resolution ADCs enable capabilities such as wideband staring signal intelligence (SIGINT) receivers, flexible software defined radio system architectures, and Low Probability of Intercept/Low Probability of Detection (LPI/LPD) radars. Fundamental performance limits of conventional ADCs significantly constrains the potential of these and other communication systems. In communication systems that transmit continuous communication signals, such as in RF communication systems, ADC technology is crucial element of system performance. Photonic devices and subsystems provide many advantages over conventional electronic ADC&#39;s (eADC) including precision timing and wide input bandwidths. Current ADC&#39;s are only capable of digitizing continuous communication signals with bandwidths of up to 10 GHz at less than 10 effective number of bits (ENOB) resolution. 
     In addition, some analog signal receivers including RF analog signal receivers, encode received analog RF signals using phase modulation. Conventional analog signal receivers that encode by phase modulation also use an amplitude channel that requires an additional amplitude modulator, and amplitude eADC&#39;s to resolve phase ambiguity that results from the phase modulation process. 
     Therefore, there is a need for an optically interleaved electronic ADC system and method to effectively overcome conventional ADC system limitations to provide an ADC capable of achieving 10 ENOB at bandwidths above 10 GHz for military and commercial operations including but not limited to radio, digital RF memory, dynamic signal modulation and wideband cueing receivers. Additionally, achieving these results in a phase modulating receiver without an amplitude channel or the additional circuitry required to support an amplitude channel would reduce the size and cost of the receiver. 
     SUMMARY OF THE PREFERRED EMBODIMENTS 
     Embodiments of a wide band analog signal receiver that converts an analog input signal into a digital output signal without an amplitude channel is disclosed. The wide band analog signal receiver includes a receiver configured to detect an analog signal comprising a voltage v(t) and a frequency f1, a pulsed laser emitting a series of optical pulses at a sampling frequency f2 with a pulsed laser, and an optical splitter configured to split the series of optical pulses into a first optical signal and an optical reference signal. The receiver also includes a phase modulator configured to phase modulate the first optical signal with the analog signal to produce a sampled optical signal such that phase shifts between adjacent samples in the sampled optical signal does not exceed π radians and a photonic signal processor configured to receive the sampled optical signal and the optical reference signal. 
     Embodiments of a method of converting an analog signal into a digital signal without an amplitude channel at a receiver are disclosed. The method includes receiving an analog signal comprising a voltage v(t) and a frequency f1, producing a series of optical pulses at a sampling frequency f2 with a pulsed laser, and splitting the series of optical pulses into a first optical signal and an optical reference signal. The method also includes phase modulating the first optical signal with the analog signal to produce an optically sampled signal such that phase shifts between adjacent samples in the sampled optical signal does not exceed π radians and receiving the optically sampled signal and the optical reference signal at a photonic signal processor. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       Exemplary embodiments are hereinafter described, wherein like reference numerals refer to like elements, in which: 
         FIG. 1  is a block diagram of an optically interleaved electronic ADC that uses an amplitude channel according to an exemplary embodiment; 
         FIG. 2  is a block diagram of an optically interleaved electronic ADC that does not include an amplitude channel according to an exemplary embodiment; 
         FIG. 3  is a simplified diagram of an analog signal receiver that does not include an amplitude channel and an I/Q signal diagram; 
         FIG. 4A  is a block diagram of a demodulator used in the photonic processor according to one exemplary embodiment; 
         FIG. 4B  is a block diagram of a demodulator used in the photonic processor according to another exemplary embodiment; and 
         FIG. 5  is a simplified block diagram of an analog signal receiver that does include an amplitude channel and an I/Q signal diagram; 
     
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
     Before describing in detail the particular improved system and method, it should be observed that the invention includes, but is not limited to, a novel structural combination of optical components and not in the particular detailed configurations thereof. Accordingly, the structure, methods, functions, control and arrangement of components have been illustrated in the drawings by readily understandable block representations and schematic drawings, in order not to obscure the disclosure with structural details which will be readily apparent to those skilled in the art, having the benefit of the description herein. Further, the invention is not limited to the particular embodiments depicted in the exemplary diagrams, but should be construed in accordance with the language in the claims. 
     With reference to  FIG. 1 , a receiver  100  can be used in a several applications including but not limited to military applications, medical imaging applications, radio applications, or any other commercial application (e.g., software defined radio, radio receivers capable of SIGINT operations, radar, digital RF memory, dynamic signal modulation, wideband cueing receivers, and sensor technology). Receiver  100  includes an RF antenna  104 . Antenna  104  receives an analog RF signal  102  at frequencies above 10 GHz, for example. In one exemplary embodiment, the photonic processor  134  included in receiver  100  enables receiver  100  to accept and process RF signals in the W-band frequency range, from approximately 75 to 110 GHz. 
     The received analog signal  102  can be input directly into photonic modulation element  106  or may be down converted prior to being transmitted to modulation element  106  to reduce the frequency of received analog signal  102  to an intermediate frequency (IF). The directly received or IF analog signal has a voltage v(t) that has a sinusoidal waveform according to one embodiment, and is used as input to amplitude  112  and phase  114  modulators. The voltage v(t) is used by modulators  112  and  114  to shape the waveform of optical pulses  122  received by pulsed laser  110 . According to the embodiment shown in  FIG. 1 , the directly received or down-converted analog signal  102  will be received by both an amplitude modulation component  112  and a phase modulation component  114 . Analog signal receiver  100  is also described in further detail in U.S. patent application Ser. No. 13/204,158 entitled “Wide Band Digital receiver: System and Method,” which was filed Aug. 5, 2011 and is incorporated by reference herein in its entirety. 
     Referring again  FIG. 1 , analog signal  102  with time varying voltage v(t) is sampled at photonic modulation element  106 . The optically sampled signal is then optically deserialized at photonic processor  134  by the optical switches and quantized at electrical analog to digital converter (eADC)  120  and processed by a digital signal processor (DSP)  138 . The eADC&#39;s  120  electronically quantize electrical signals detected by the balanced detectors shown in photonic processor  134  and transmit the quantized electrical signals to digital signal processor  138 , which outputs the digital information  144  originally contained in analog signal  102  for further application specific processing. The control electronics  140  used to control the pADC  130  of the W-band receiver  100  provide on-board eADC calibration, timing control, memory, and data processing to ensure effective and proper operation of the W-band receiver  100 . The control electronics  140  can be enabled by way of a PC-based applications program, such as a Labview program, which provides system level instrument control, calibration, and real time data analysis. The analysis may also include the ability to calculate a least squares fit to the digitized signal in order to determine ENOB. Also, a Fourier transform calculation may be used to determine the SFDR (as computed by the PC-based applications program). 
     Photonic processor  134  utilized in the wide band receiver  100  can provide a scalable architecture referred to as multi-dimensional quantization (MDQ). One technical benefit of the MDQ system and method is an ability to increase the ENOB of the photonic ADC over that of the constituent electronic ADCs. MDQ technology also increases the SFDR of the photonic ADC over that of the constituent electronic ADCs and uses optical or hybrid optical/electrical deserialization to reduce the effective sampling rate presented to each electronic ADC. MDQ systems and methods also allow for simple correction for various imperfections of the optical receiver. For example, it allows for increasing the instantaneous bandwidth (IBW) of a wide band receiver to up to 35 GHz while maintaining a resolution of around 8 ENOB. Details of some examples of such photonic processors are described in U.S. Pat. No. 7,876,246, and U.S. Pat. No. 7,868,799, which are incorporated in their entirety herein by reference. 
     Referring again to  FIG. 1 , an analog signal  102  received by an antenna  104  is phase and amplitude encoded onto a stream of optical pulses generated by an optical laser such as a low phase noise mode locked laser (MLL)  110 , for example. Performing the sampling process using phase modulated optical pulses, as contrasted to simply relaying the RF signal on a phase modulated continuous wave optical carrier to an electronic ADC for sampling, is critical. Optical sampling allows the sampling to occur using an ultra-low jitter optical pulse source  110 . Without the low jitter associated with optical sampling, the above benefits cannot be realized, because the performance will be limited by the clock jitter on the clock that drives the electronic ADCs. 
     Alternatively, the amplitude modulator (AM) can be provided with an input directly from a mixer or low noise amplifier (LNA) instead of from the antenna  104 . The resultant optical pulses are demodulated on three separate channels including In-phase (I) and Quadrature (Q) data resulting from optical hybrid I/Q demodulation of signals from the optical phase modulator  114  and the un-modulated channel in optical modulation element  106 , and amplitude data transmitted from optical amplitude modulator  112 . One purpose of photonic processor  134  is to deserialize the sampled analog signal  102  with optical switches such that each of the three separate channels may be provided in parallel prior to being converted to electrical signals to effectively overcome the limitations of the relatively low speed photodiodes and electrical quantizers. Accordingly, the collective sampling rate of electrical quantization element  136  can be greatly increased depending on the number of parallel paths and the particular configuration of elements  134  and  136 . 
     In the embodiment shown in  FIG. 1 , the optical switches provided on the I, Q, and amplitude channels time deinterleave each channel to by providing serial to parallel conversion in each optical channel according to timing signals derived from the optical pulse train from MLL  110 . At modulation element  106 , an optical signal from laser  110  is provided to amplitude modulator  112  to create a separate amplitude channel which is used by electrical quantizer  136  to remove any phase ambiguity introduced into the phase modulated signal in cases where the phase modulator  114  is driven through more than one 2π phase rotation. The concept of phase ambiguity in the context of I/Q demodulation is discussed in detail with respect to  FIG. 3  and  FIG. 5 . 
       FIG. 3  depicts a simplified analog signal receiver  300  including a microwave sampler that does not include an amplitude channel as well as an I/Q signal diagram  302 . The simplified receiver  300  can be applied to the analog signal receiver of shown  FIG. 2  that includes optical interleaving in a photonic processor,  240  but can included many other types of analog signal receiver. Specifically, signal v(t)  306  phase modulates the series of optical pulses from laser  304  passing through the phase modulator  308  such that only the phase of the optical pulses are changed. The phase modulated signal is then demodulated at I/Q demodulator  360  using reference signal  310 , also provided by laser  304 . 
     At I/Q demodulator  360 , the in phase I signal, which is proportional to sin [v(t)], is detected by photodectors  318  to produce electrical signal  320 . Furthermore, the quadrature Q signal is phase shifted 90 degrees at element  340  in I/Q demodulator  360  such that it is proportional to cos [v(t)]. When Q signal  310  is detected by photodetectors  318 , electrical signal  322  is produced. Polar coordinate system  302  graphically depicts the relationship between the Q signal  322  (shown as an extension from x axis  334 ) and I signal  320  (shown as an extension from y axis  332 ). The outputs from the I/Q demodulator  360  may be depicted in two dimensional I/Q space  302 . 
     In the simplified system  300 , the amplitude of the vector shown in I/Q space  302  remains constant because phase modulator  308  only alters the phase of the optical pulses from laser  304  rather than amplitude. However, phase angle φ  330  changes as a result of the differences between signal  320  and signal  322 , causing the displayed vector to spin about I/Q space  302  in a manner proportional to the phase modulation applied at phase modulator  308 . Accordingly, the phase angle  330  is proportional to the voltage v(t)  306  applied to the phase modulator  308  and so can be used to determine the received signal v(t). 
     Because the phase angle  330  is proportional to any received voltage v(t), the phase angle  330  may rotate any number of times about I/Q space  302  comprising 360 degrees of rotation, or 2π radians of rotation. When phase angle  330  is limited to 2π radians of rotation, the corresponding voltage can be determined mathematically by taking the arctangent of the detected I signal  320  (approximated as a sine wave) divided by the Q signal  322  (approximated as a cosine wave), for example. However, if the phase angle exceeds 2π radians of rotation, a single phase angle will correspond to two different input voltages v(t)  306  causing phase ambiguity. Phase ambiguity of this kind is depicted in I/Q graph  502 . As seen in  502 , when phase angle  502  exceeds 2π radians of rotation, the phase only provides a single vector coordinate, resulting in phase ambiguity. 
     Some analog signal receiver systems  100  have resolved phase ambiguity by counting each 2π radian phase rotation by using an additional amplitude channel  112  as shown in a simplified analog signal receiver depicted in  FIG. 5 . Receiver systems  100  keep track and distinguish between 2π phase rotations by detecting the amplitude of the analog signal v(t) as shown by graph  506 , which depicts the input voltage v(t) at three different levels  514 ,  516 , and  520  and each voltage levels respective phase rotation. 
     However, according to one disclosed embodiment as shown in  FIG. 2  and  FIG. 3 , the phase ambiguity that results from the phase angle  330  exceeding 2π radians of rotation is resolved in another manner. According to one embodiment, analog input signal  306  is a sinusoidal signal with a frequency f1 and a peak to peak voltage of V2 while phase modulator  206  requires a voltage of V1 to induce a it phase rotation and laser  210  has a sampling frequency f2. By setting variables such as the peak to peak voltage (V2) and frequency (f1) of received analog signal v(t)  306 , as well as the sampling frequency (f2) of laser  210  and the amount of voltage (V1) required by phase modulator  206  to induce a it phase rotation, the resulting phase angle rotation can be limited to a rotation of 2π radians or less, thereby eliminating phase ambiguity and the need for an amplitude phase tracking channel. 
     According to one exemplary embodiment, the following equations ensure that the resulting phase angle rotation  330  is limited to a rotation of 2π radians or less. As stated previously, phase modulator  308  and I/Q demodulator  214  cause the phase angle at any given time, φ(t) to be equal to the received analog voltage v(t) at any given time such that equation (1) holds true. Furthermore, the characteristics of phase modulator  308  will dictate the value of a voltage V1 required to induce a it radian phase rotation such that equation (2) is also true. Additionally, because v(t) is a sinusoidal signal with a frequency f1 and a peak to peak voltage of V2, according to one embodiment, equation (3) is equivalent to equation (2), wherein t is the time between optical samples, or equivalently the inverse of the sampling rate, f2.
 
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     Furthermore, because each voltage V1 that results in a it radian phase rotation must be less than or equal to a it radian phase rotation to ensure that no voltage corresponds to a radian phase rotation greater than 2π, equation (4) must also result. Replacing t with the inverse of the sampling rate, f2 results in equation (5). 
     
       
         
           
             
               
                 
                   
                     
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     Accordingly, if the analog signal receiver depicted in  FIG. 2  is designed such that equation (5) holds true, the resulting phase angle rotation can be limited to a rotation of 2π radians or less, thereby eliminating phase ambiguity and the need for an amplitude phase tracking channel. For example, using equation (5) as a guide, if laser  210  is set to oscillate such that optical pulse stream  222  has a sampling rate of 20 Gs/s or frequency of 20 Ghz, phase modulator  206  is selected such that a 2 volt signal induces a it phase rotation, and that input analog signal  102  has a peak to peak voltage of 16 volts, the analog signal receiver shown in  FIG. 2  can accept analog input signals with frequencies up to 1.6 GHz and will be able to accurately detect analog signal  102  without phase ambiguity and without the need for an amplitude channel  112  as shown in  FIG. 1 . Furthermore, using equation (5) as a guide, the analog signal receiver shown in  FIG. 2  can be designed to accept any number of maximum input frequencies. 
     Referring to the general operation of the analog signal receivers depicted in  FIG. 2 , the performance of the photonic processor  134  is determined by the low phase noise of the pulsed laser  110  while the aperture window is defined by the optical pulse width that samples the RF waveform  102  at the phase modulator  114 . With respect to phase noise, a MLL  110  provides better performance than by using a continuous wave (CW) laser as it produces an optical pulse train with lower jitter and higher resolution rate optical pulses. A photonic sampling element  106 , encodes the analog signal  102  onto the phase and amplitude of the optical pulse stream. A photonic processor  134  contains components for optical deserialization, I/Q demodulation, and optical to electrical detection. 
     An electronic quantization stage  136 , also referred to herein as a digitizer, includes multiple eADC&#39;s  220  per optical channel, with associated calibration, memory and processing functionality according to one exemplary embodiment. The number of eADC&#39;s per electrical channel, such as two, four, five, or more, may be utilized in the digital platform while remaining within the spirit and scope of the invention. According to one embodiment the number of eADC&#39;s is dependent on the number of time deinterleaved channels that are implemented at the optical switches shown in photonic processor  134 . In addition, control electronics  140  are functionally connected to photonic processor  134  and electronic quantizer  136  to incorporate the various processes disclosed herein and to provide overall system management. Control electronics  140  may comprise at least one processor and at least one memory so that the control electronics processor can carry out instructions stored in the memory. 
     Referring to  FIG. 2 , optical pulse train  222  emitted from MLL  210  at a predetermined rate such as 20 Gs/s is provided to an optical splitter. At the splitter the energy of optical pulse train  222  is split between the two output ports, one optical signal  206  optically samples analog signal  204  at phase modulator  228  at a rate of 20 Gs/s while one optical signal  210  remains un-modulated as a reference signal. According to other embodiments, splitter divides optical pulse stream  222  into three separate channels, with a third channel being sent to an amplitude modulator as in  FIG. 1 . 
     Referring again to  FIG. 2 , after phase modulation by the RF or other analog signal  102  with a voltage v(t), the optical phase modulated signal  212  and optical reference signal  210  are optionally sent to a deserializer which may include optical switches for phase modulated signals  212  and for reference signals  210  that are both controlled by a common timing signal derived from laser  210 . Each optical switch can be a lithium niobate switch, such as one made by E-O Space Inc., according to one exemplary embodiment. 
     In both  FIG. 1  and  FIG. 2 , I/Q demodulators, shown in greater detail in  FIGS. 4A and 4B , will receive de-interleaved phase modulated and reference optical signals with a reduced sampling rate. Each of the I/Q demodulators  214  may be a 90° optical hybrid demodulator shown as element  400  in  FIG. 4A  with two balanced photodetectors  410  and  412  to convert the received optical signals into electrical I and Q signals. I/Q demodulators  400  may be demodulators such as ones made by Optoplex, Inc. However, the I/Q demodulators are not limited to 90° optical hybrid demodulators and may include 60° demodulators or any other variation of an I/Q demodulator. Each balanced photodetector  410 ,  412 ,  424 ,  426 , and  428  can be a InP, 20 GHz bandwidth balanced photodetector, such as one made by U 2 T Inc. Other commercially available switches, I/Q demodulators, and balanced photodetectors may be used in the receiver  100  as shown in  FIG. 1 , while remaining within the spirit and scope of the invention. By using such devices in a preferred implementation of the first embodiment, receiver  100  is well suited for heterogeneous Si/InP chip scale integration, which is highly desirable for military and other applications that require durable and long-lasting components. 
     Once the optical I and Q channel signals have been converted to analog electrical signals by the balanced photodetectors, the electrical signals are quantized by eADC&#39;s  220  as shown in  FIG. 2  at a rate determined by the clock frequency  228  provided by timing control electronics  240 . 
     It is understood that while the detailed drawings, specific examples, material types, thicknesses, dimensions, and particular values given provide a preferred exemplary embodiment of the present invention, the preferred exemplary embodiment is for the purpose of illustration only. The method and apparatus of the invention is not limited to the precise details and conditions disclosed. For example, although specific types of optical component, dimensions and angles are mentioned, other components, dimensions and angles can be utilized. Also, receiver  100  may be implemented in a wide band RF stage system or any other type of high-frequency band receiver, such as receivers operating in the 70 GHz to 200 GHz and up range. Various changes may be made to the details disclosed without departing from the spirit of the invention which is defined by the following claims.