Abstract:
An acoustical noise reduction system which comprises a primary acoustic to electric transducer, digital signal processor (DSP), an electric to acoustic transducer, and a secondary acoustic to electric transducer is disclosed in the present invention. The active noise reduction system is located close to the noise source with the sound being sensed by a primary transducer before the noise enters the active noise reduction area. The system functions to generate an anti-noise cancellation sound wave with an acoustic propagation speed of approximately 330 m/sec and an electromagnetic propagation speed of approximately 3×10^8 m/sec.

Description:
FIELD OF THE INVENTION 
     This invention relates to active acoustical noise reduction systems. 
     BACKGROUND OF THE INVENTION 
     Formulating practical solutions for the reduction of problematic noise is an active area of engineering research in both the fields of acoustics and control. To date, noise reduction has been mostly carried out using passive means. These passive methods almost always require the installation of heavy, bulky and costly materials such as foams, wools and fibrous bats. The additional weight bulk and physical change required is in many situations neither practicable nor cost effective. Also, one of the fundamental problems with insulators or absorbing materials is that they do not work well at reducing noise at the low frequencies. This is primarily because the acoustic wavelength at low frequencies becomes large compared to the thickness of typical absorbent materials. Furthermore, all existing noise reduction systems utilize the feedback technique in closed environments, which are not ideal for the cancellation of random noise. 
     For example, U.S. Pat. No. 7,853,024 issued to Slapak et al., discloses an active noise control for controlling a noise produced by a noise source. The prior art&#39;s complicated prediction is based on the received signal (noise samples) and does not involve a primary transducer that senses the signal ahead of time to account for the dynamic changes of the random noise. 
     Active noise reduction can overcome these problems and disadvantages. Active noise reduction is based on the principle of superposition of signals. According to the principle of superposition, if two signals exist, one an undesired disturbance, the other a controlled response, their combined effect can be made zero if they are equal in magnitude and opposite in phase. This signal cancellation phenomenon is commonly termed destructive interference, and is a basis for the operation of active noise reduction systems. 
     The advantages of active noise reduction are numerous. However, the two most significant relate to the method&#39;s spectral effectiveness and method of installation. 
     Active noise reduction exploits the long wavelengths associated with low frequency sound. Active noise reduction systems are, therefore, more effective at attenuating low frequency acoustic disturbances. Such low frequency disturbances are the common undesired side effect of operating machinery and are difficult to reduce using passive techniques. 
     In terms of physical implementation, active noise reduction systems typically comprise small and light weight components. This means that active noise reduction systems can be used in many situations where passive methods are impractical due to their bulk, weight and cost effectiveness. 
     The existing active noise reduction systems still suffer from their own disadvantages, however. These include the risks associated with system stability, less than adequate noise suppression performance and insufficient operating bandwidth. 
     Active noise reduction systems based on a feedback control approach, for example, risk instability, particularly where the feedback compensator has no means of accounting for change in the dynamic characteristics of the plant. It is difficult to design a feedback compensation network that provides both highly effective and robust noise reduction, particularly over a wide frequency bandwidth. Also, as the feedback compensator&#39;s gain is increased to improve low frequency noise suppression, amplification at the higher frequencies typically impacts negatively on performance. 
     Active noise reduction systems based on the known adaptive feed-forward technique, for example, can experience problems with effective parameter convergence and therefore provide less than optimal performance. Adaptive techniques also require intensive processing particularly where the feed-forward path dynamics are complex and the time available to compute a control response is brief. In many cases this makes this method of control unfeasible due to cost or the inability to implement the system practically. 
     SUMMARY OF THE INVENTION 
     It is a main purpose of this invention to provide for optimal noise reduction capabilities for a variety of noise fields without the use of any feedback technique. The present invention is an active acoustic noise reduction system that comprises sensors at a distance near the source of the noise, which feeds the sampled noise in the electrical media to the main system. In one embodiment, these sensors could be in the form of a microphone, piezo, motion sensor, etc. In another embodiment, the electrical media could be wired or wireless. The system takes advantage of the received electrical noise signal a delta time ahead of the arrival acoustic noise, thus utilizing an appropriate self-adjusting timing process to cancel the noise with out-of-phase acoustical energy. 
    
    
     
       BRIEF DESCRIPTION OF THE FIGURES 
       The invention can be better understood with reference to the following figures. The components in the figures are not necessarily to scale, emphasis instead being placed upon illustrating the principles of the invention. Moreover, in the figures, like reference numerals designate corresponding parts throughout the different views. 
         FIG. 1  generally shows one embodiment of the active noise reduction system. 
         FIG. 2  is a schematic block diagram depicting one embodiment of an active noise reduction system with a direct noise source input with no interference. 
         FIG. 3  is a schematic block diagram depicting one alternative embodiment of an active noise reduction system with a direct noise source input with no interference. 
         FIG. 4  is a schematic block diagram depicting another possible embodiment of an active noise reduction system with a direct noise source input with no interference. 
         FIG. 5  is a schematic block diagram depicting another embodiment of an active noise reduction system with an indirect noise source input transmitted through a boundary. 
         FIG. 6  is a schematic block diagram depicting yet another alternative embodiment of an active noise reduction system; 
         FIG. 7  is a schematic block diagram depicting yet another alternative embodiment of an active noise reduction system; 
         FIG. 8  is a schematic block diagram depicting yet another alternative embodiment of an active noise reduction system; 
         FIG. 9  is a schematic block diagram depicting steps  1 - 2  of an auto-calibration procedure; 
         FIG. 10  is a schematic block diagram depicting steps  3 - 6  of an auto-calibration procedure; and 
         FIG. 11  is a schematic block diagram depicting step  7  of an auto-calibration procedure. 
     
    
    
     DETAILED DESCRIPTION 
     Some embodiments of the present invention are described in detail with reference to the related drawings of  FIGS. 1 through 5 . Additional embodiments, features and/or advantages of the invention will become apparent from the ensuing description or may be learned by practicing the invention. 
       FIG. 1  generally shows one embodiment of the active acoustic noise reduction system  100 . A noise source  1  at the beginning of the diagram is sensed by the primary transducer  2 , which then feeds the sampled noise, in the form of an input signal  102 , through either wired or wireless means into a digital signal processor (DPS) within the main system. The DSP  23  then feeds into an electric to acoustic transducer  18 . The acoustic propagation speed of the noise is approximately 340 m/sec, which correlates to the sound wave that is being cancelled. It is significant to note that the present invention addresses sound waves, and not electromagnetic waves, as the aforementioned 340 m/sec indicate. The system takes advantage of the received electrical noise signal a delta time ahead of the arrival acoustic noise, thus generating a process to cancel the noise with out-of-phase acoustical energy. The system functions to generate an anti-noise cancellation sound wave. 
     Referring to  FIG. 2 , a more schematic block diagram of the active noise reduction system is shown. Similar to  FIG. 1 , a noise source  1  at the beginning of the diagram is sensed by the primary transducer  2 , which then feeds the sampled noise through either wired or wireless means into the main system. Within the system, the noise passes through an anti-aliasing filter  3  before entering into an Analog-to-Digital converter  4 . The converted noise signal in digital format is sent continuously to a dual port RAM  5 , the main storage, which then wraps around when the write address reaches the end location. The number of the addresses of the main storage, dual port RAM  5 , shall be big enough to accommodate up to a few seconds worth of noise samples. 
     A specific depth of sampling storage  6  (bank of shift registers) scans through the entire main storage  5 , and its output is used to run convolution in the match filter  11 . As illustrated in the double arrow of  FIG. 2 , the sampling storage  6  scans and reviews at least a portion of the converted noise signal in digital format that is transmitted to the main storage  5 . The same noise signal propagates acoustically and is sensed by the secondary transducer  7  placed at the near field, which feeds the local (delayed) noise through either wired or wireless means into the main system. 
     A fixed amount of converted noise samples in digital format can be stored in sampling storage  10  (smaller bank of shift registers). The outputs of both storages  6  and  10  undergo convolution in the match filter  11 , which synchronizes the stored sample gathered in the primary transducer  2  to the truncated signal from the secondary transducer  7  in time domain. 
     The timing control logic  12  then determines the delta time between  2  and  7 , in terms of offset in address count, for the dual port RAM  5 . While the noise sample from primary transducer  2  is consistently written into main storage  5  by the write logic  13 , the output of the dual port RAM  5  is then accessed with the read logic  14  lagging with the offset derived from the match filter  11 . Both the write logic  13  and the read logic  14  advance with the same clock, so the output of the main storage  5  shall align with the signal received at the secondary transducer  7 . The actual offset used in the device accounts for all the circuits&#39; delay. 
     The acoustic energy of the noise source  1  received at secondary transducer  7  shall be much attenuated from the signal received at primary transducer  2 , due to the field energy is reciprocal to square of distance. There is a gain ratio estimator  16 , which takes the outputs of main storage  5  and sampling storage  10 , and compares their gain ratio from accumulating positive signal samples in fixed time duration. The derived ratio feeds into the gain setting device  17 , which drives the transducer  18 . The transducer  18  converts the electrical energy into acoustic energy with inverted polarity. Thus the acoustic output of this device is aligned with the incoming noise but in opposite phase, in order to cancel out the incoming noise. 
     As referenced in  FIGS. 9-11 , the speed of the sound wave changes with temperature and humidity, so the device has to calibrate the time alignment periodically. Below is the sequence of events for calibration: 
     Step  1 : Gauge the delta time t 1  between the primary transducer  2  and the secondary transducer  7  by turning off the transducer  18 , so that there is only an acoustic signal from noise source  1  between the primary transducer  2  and the secondary transducer  7 . The delta t 1  will be implemented in offset between the write address and the read address of the Dual Port RAM  5 . 
     Step  2 : The timing control logic  12  initiates writing converted samples on both  6  and  10  sampling storages, while storage  10  is shorter and wraps around when the counter reaches its end location. Timing control logic stops writing on both storage when sampling storage  6  reaches its capacity. 
     Step  3 : The timing control logic  12  starts convolution by sliding the samples in storage  6  to run multiplication and accumulation on each sample taps in storage  10 , and generates a series of the product terms in separate storage in match filter  11 . 
     Step  4 : Match filter  11  looks for the greatest value in the product terms, and use the corresponding index as the max point. The offset value of delta t 1  is M+N−max point, where M is the length of the storage  6 , N is the length of the storage  10 , and max point is the index of the greatest product in separate storage in match filter  11 . 
     Steps  5 - 10  illustrate the process of calibration between the MIC2 storage  10  and the transducer  18 . 
     Step  5 : Gauge the delta time t 2  between the secondary transducer  7  and transducer  18 , by switching off the primary transducer  2  and replaying the stored samples in storage  6 , from Steps  1  through  4 . The secondary transducer  7  picks up the reproduced sound from transducer  18 . 
     Step  6 : The timing control logic  12  initiates writing converted samples from the secondary transducer  7  to storage  10 , while reading through storage  6 . The storage  10  is shorter and wraps around when the counter reaches its end location. The timing controller calculates the correct timing in terms of the reading address offset from the writing address by stopping any writing to the storage  10  when storage  6  reaches its end point. 
     Step  7 : The timing control logic  12  starts convolution by sliding the samples in  6  to run multiplication and accumulation on each sample taps in storage  10 , and generates a series of the product terms in separate storage in match filter  11 . 
     Step  8 : Match filter  11  looks for the greatest value in the product terms, and uses the corresponding index as the max point. The offset value of delta t 2  is M+N−max point, where M is the length of the storage  6 , N is the length of the storage  10 , and max point is the index. 
     Step  9 : Gauge the gain ratio between the primary transducer  2  and secondary transducer  7  with gain controller  16 . The gain controller takes the outputs of main storage  5  and the storage  10 , already aligned in the time domain and compares their magnitude ratio from accumulating positive signal samples in fix time duration. The ratio will be applied to the output of the main storage  5 , before entering into the Digital-to-Analog Converter (DAC)  15 . 
     Step  10 : The system uses the delta time t 1  and delta time t 2 , plus the ratio into the resulting anti-phase noise signal. All these parameters account the process delay of all the specific hardware, trying to achieve the best approximation to cancel the incoming random noise. Every calibration step is executed in a preset time interval, event triggered, or user override mode in order to account for environmental changes (e.g., temperature, humidity etc). 
     Sometimes, the noise to be cancelled is periodic with Fourier harmonics in nature, and it is not practical to use a match filter to synchronize the controlled response to the incoming undesired disturbance. A dedicated signal source  24  as depicted in  FIG. 3  with a pre-determined random pattern encoded in acoustic bandwidth is necessary to calibrate the invention. Such a device produces a burst of noise through the primary transducer  2  and the secondary transducer  7 , triggered by the timing controller  12 . Steps  1  through  10  are then performed to gauge the delta time t 1  between the primary transducer  2  and the secondary transducer  7 . This method does not need to be performed in a controlled environment, as this special burst of noise can be superimposed in the existing background noise. The uniqueness of the random noise increases the effectiveness of the match filter  11 . 
     The dedicated signal source  24  in  FIG. 3  can be replaced by transducer  18  to calibrate the invention. The burst of noise can be generated from an embedded Pseudo Noise Generator  25  as shown in  FIG. 4 , triggered by the timing controller  12 . In this measurement the transducer  7  receives the pre-defined acoustic pattern from transducer  18  with a delta time t 1  ahead of transducer  2 . The invention undergoes Steps  1  through  10  to gauge the delta time t 1 . The uniqueness of the random noise increases the effectiveness of the match filter  11 . 
     In practical applications, there are certain types of physical boundaries between the primary transducer  2  and the rest of the system, including but no limited to a wall, building, bushes, etc, and the acoustic noise travels through the boundary would be altered in frequency domain. In most cases, the transfer function is more similar to a low pass filter with attenuation, and the above system implemented in time domain is adequate enough to cancel the random noise. 
     As referred to in  FIG. 5 , in order to optimize in frequency domain, there are extra logic blocks added to account for the transfer function between the primary transducer  2  and secondary transducer  7 , assuming the primary transducer  2  has the same frequency response with the secondary transducer  7 . 
     Turning now to  FIGS. 6 ,  7 , and  8 , the steps are continued. Step  11 : After steps  1  through  8 , a FFT 1 block  19  is shown using samples from the main storage  5  output that are already aligned with samples from secondary transducer  7  in the time domain, while FFT2 block  20  is shown using samples from storage  10 . 
     Step  12 : A DSP block  21  is used to derive the transfer function between the primary transducer  2  and the secondary transducer  7 , while the secondary transducer is the numerator. All the coefficients are stored in the Finite Impulse Response (FIR) block  22 . 
     Step  13 : The FIR block  22  is used to implement the transfer function on the output of the main storage  5  (dual-port-RAM), with its read control logic  14  capable of being adjusted with the delay of the additional FIR block, before entering the DAC  15 . The resulting signal is amplified by gain stage  17  to drive the transducer  18  with opposite polarity, and now the generated output shall cancel out the noise signal perceived at secondary transducer  7 . 
     While the invention has been described in terms of various specific embodiments, those skilled in the art will recognize that the invention can be practiced with modification within the spirit and scope of the claims. Additionally, features illustrated or described as part of one embodiment can be used in another embodiment to provide yet another embodiment such that the features are not limited to the specific embodiments described above. Thus, it is intended that the present invention cover all such embodiments and variations as long as such embodiments and variations come within the scope of the appended claims and their equivalents.