Abstract:
A suppression system of background noise of speech signals uses an adaptive filter of long-time and short-time statistical characteristics of the speech signals. Since the statistical characteristics of the speech signals vary with time, the associated coefficents of the filter also have to be adjusted according to the varitation of the speech signals to eliminate the unnecessary background noise. High frequency attenuation of the speech signals is compensated for by passing the signal through a high frequency booster to elevate the degree of brightness of the speech signals and to improve their quality.

Description:
BACKGROUND OF THE INVENTION 
   1. Field of the Invention This invention relates to a kind of suppression system of background noise of speech signals and the method thereof. The suppression system of background noise of the invention focuses on the short time and long time characteristics of speech signals and the method thereof. 
   2. Description of the Prior Art 
   Voice sound signals are a major data type transmitted in telecommunication systems. During the process of communication, in addition to the voice sounds, background noise of the telecommunication environment also enters into the telephone, and will cause some degree of interference and influences the quality of the telecommunication. In particular, recent rapidly-growing mobile phone use is easily influenced by the background noise. So the technology of suppression of background noise is one important topic relating to quality of current telecommunication systems. There are three kinds of technology commonly used for the suppression of background noise, as follows: 
   The first method is the method of deleting the noise in the frequency domain. The basic principle of this method is to estimate the energy of the noise within the frequency domain in a segment of non-speech sounds, and then to eliminate the estimated energy of the noise at each frequency in the frequency domain in the speech segments that follow. Although this method is simple, its effect on suppression of background noise is limited, since the statistical characteristics of the general background noise varies with time. This method of suppression of noise is disclosed in U.S. Pat. No. 6,175,602 and 5,742,927. 
   The second method is the method of deleting the background noise in the time domain. The basic principle of this method is utilization of two microphones to receive the outside signals. The Primary microphone is used to receive the speaker&#39;s voice along with the background noise. The secondary microphone is used to receive only the background noise. Thus, the background noise could be estimated through the secondary microphone. Next, by subtracting the estimated background noise from the signal of the first microphone in the time domain, better quality speech signals can be obtained. However, this method requires two microphones and there must be a sufficient distance between these two microphones, which is nearly impossible for mobile phone applications. 
   The third method is the periodic tracking method. The basic principle of this method is to estimate and track the periods of voice signals first, and next to find the average of the related signals within a few periods. The enhancement of speech is achieved by averaging the delayed and weighted versions of input speech signals, where the delay lengths correspond to the detected pitch periods. Since background noise does not possess the same pitch periods as the original speech, it is cancelled out by this operation. The concept of using subtraction with periodic tracking is disclosed in U.S. Pat. 5,598,158. 
   It could be found from the above mentioned methods that there still are many drawbacks in the above-mentioned technologies and there is a urgent need for improvement. 
   SUMMARY OF THE INVENTION 
   The purpose of this invention is to provide a suppression system and method of suppression of background noise in speech signals wherein it constructs the model of the speech signals by utilizing one all-pole linear prediction filter and also detects the pitch periods which only exist in the speech signals, and it reduces the background noise according to the estimated associated speech signal coefficients and the estimated speech signal pitch periods which further enhances the quality of the voice sounds signals. 
   Another purpose of this invention is to provide a system of suppression of background noise of speech signals and the method thereof which could largely elevate the quality of the input signals with a low signal-to-noise ratio, as well as adjust the related coefficients adaptively. 
   Yet another purpose of this invention is to provide a system of suppression of background noise of speech signals and the method thereof which has low degree of complexity and requires only one microphone, so that it is fairly suitable to be used with mobile phones and the technology of speech recognition, so as to enhance the quality of speech coding and the recognition rate of speech signals. 
   The background noise suppression system for speech signals is used to enhance the decrease in the quality speech signals caused by the influence of background noise. The analog speech signals are transformed into digital ones first through the sampling unit for further digital signal processing. The bandwidth of the voice sounds is about 4 KHz. According to the Nyquist sampling principle, the minimum required sampling frequency is 8 KHz. In order to elevate the degree of correlation between these sampling signals, the sampling frequency is increased from 8 KHz to 32 KHz, which is called “oversampling”. The digital signals after sampling are represented using a 12 bit pulse Code Modulation (PCM) technology. That is to say, the allowable variation range of the digital sound samples is within ±2048. 
   The system and the method of suppression of background noise of speech signals of this invention comprises: one oversampling unit, two low-pass filter units, one adaptive speech analysis unit, one pitch detection unit, one background noise suppression unit, and one high-frequency booster unit. Let us assume that the speech signals containing the background noise is S n (t); first S n (t) is oversampled by the oversampling unit with a sampling rate that is much higher than the Nyquist rate to increase the correlation between speech samples. Next, we represent the digit signals S n (k) acquired by oversampling with 12 bit pulse code modulation, wherein k represents the k-th sampling signal. Due to the effect of the oversampling unit, it is required to remove unnecessary signals outside the speech signal bandwidth by the use of a low-pass filter. The digital signal, S nn (k), through the first low-pass filter is sent into the adaptive speech analysis unit, the pitch detection unit, and the background noise suppression unit, respectively, to advance the process to the next step. In the adaptive speech analysis unit, an N&#39;th order all-pole adaptive filter is utilized to estimate the speech signals. The coefficients of the all-pole adaptive filter is a l (k), i={1,2, . . . N}, which is determined to represent the unique characteristics of the speech signals, will be sent into the background noise suppression unit. Further, S nn (k) will be sent into the pitch detection unit to estimate the pitch periods of the speech signals, wherein the estimated pitch period P range is within 3-10 ms. If the sampling frequency is 32 KHz, then the number of samples corresponding with one pitch period is about 96-320. The pitch periods for each speech signal will be estimated and sent to the background noise suppression unit for use in the next step of suppression of the background noise. 
   The suppression filter unit utilizes the filter coefficient, a i (k), and the speech signal pitch period, P, estimated from the adaptive speech analysis unit and the pitch detection unit, respectively, to design the background noise suppression unit. The S nn (k) from the first low-pass filter is sent into the background noise suppression unit to reduce- the energy of the background noise embedded in the speech signals and enhance the speech signal-to-noise ratio. Since the high-frequency components in the original speech signals are also suppressed by the background noise suppression unit, another high-frequency booster is used to compensate for the suppression component of high frequencies in the speech signals. Finally, another low-pass filter is used to filter the noise outside the bandwidth of the speech signals. The speech signal, Ŝ n (k), with elevated quality is thus acquired. 

   
     BRIEF DESCRIPTION OF THE DRAWINGS 
     The drawings disclose an illustrative embodiment of the present invention which serve to exemplify the various advantages and objects hereof, and are as follows: 
       FIG. 1  is the schematic diagram of the suppression system of speech signal background noise of this invention; 
       FIG. 2  is the circuit block diagram of the adaptive speech analysis unit of said suppression system of speech signal background noise; 
       FIG. 3  is the circuit block diagram of the adaptive prediction filter coefficient of said suppression system of speech signal background noise; 
       FIG. 4  is the circuit block diagram of the pitch detection unit of said suppression system of speech signal background noise; and 
       FIG. 5  is the circuit block diagram of the background noise suppression unit of said suppression system of speech signal background noise. 
   

   REPRESENTATIVE SYMBOLS OF MAJOR PARTS 
   
       
         101  oversampling unit 
         102  low-pass filter 
         103  adaptive speech analysis unit 
         104  background noise suppression unit 
         105  pitch detection unit 
         106  high-frequency booster 
         107  low-pass filter 
         21  hard limiter 
         221  adaptive stepsize decision unit 
         23  adaptive prediction filter 
         31  hard limiter 
         41  pitch decision unit 
         51  noise shaping filter 
     
  
   DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT 
   Please refer to  FIG. 1 , the suppression system of background noise of speech signals of this invention comprises: one oversampling unit  101 , two low-pass filters  102 ,  107 , one adaptive speech analysis unit  103 , one pitch detection unit  105  one background noise suppression unit  104 , and one high-frequency booster  106 . Before proceeding with suppression of background noise, analog speech signals are transformed into digital signals which are suitable for further processing including processing through an oversampling unit and low-pass filter. The oversampling unit  101  performs analog-to-digital transformation on analog speech signals and represents the transformed digital signal with a pulse code modulation (PCM) technique. In the analog-to-digital transformation, the sampling frequency is far larger than the minimum frequency required by the sampling principle to enhance the correlation between samples. In this embodiment, the suggested sampling frequency is 32 KHz, which is 8 times the bandwidth of the general speech signal bandwidth of 4 KHz. Low-pass filter  102  is used to remove the noise outside the bandwidth of the speech signals, especially that the oversampled signals are passed through oversampling unit  101  and it is necessary to limit the bandwidth of the signal within the bandwidth of the speech signals with one low pass filter  102  to elevate the performance of the following process units. In this embodiment, it adopts one third-order Butterworth low-pass filter, wherein the cut-off frequency is designed at the bandwidth of the speech signals, which is 4 KHz. The signal S nn (k) from the low-pass filter is sent into the adaptive speech analysis unit  103 , the pitch detection unit  105 , and the high-frequency booster  106 , respectively, to proceed to the next stage process. 
     FIG. 2  is the circuit block diagram of the adaptive speech analysis unit. The adaptive speech analysis unit  103  comprises one hard limiter  21 , one stepsize estimation unit  22 , and one adaptive prediction filter  23 . The hard limiter  21  decides the output bit, b(k), by comparing the input speech sample, S nn (k), and the prediction S e (k) from the adaptive prediction filter  23 , as shown in the following equation: 
               b   ⁡     (   k   )       =     {           1   ,       if   ⁢           ⁢       S   nn     ⁡     (   k   )         &gt;       S   e     ⁡     (   k   )                       -   1     ,       if   ⁢           ⁢       S   nn     ⁡     (   k   )         &lt;       S   e     ⁡     (   k   )                           (   1   )               
   The stepsize estimation unit  22  estimates the stepsize of the current samples by utilizing the bit determined beforehand. The estimated stepsize is used to compensate for the residual signal, which is the unpredicted part of the last prediction sample. Let us assume that the currently determined bit is b(k), then the adaptive stepsize decision unit  221  in the stepsize estimation unit  22  will determine the current status of the adaptive speech analysis unit  103  according to b(k) and its preceding three bits, b(k−1), b(k−2), and b(k−3), and determine one correction coefficient, α(k), as shown in Table 1. Next, it produces one estimated stepsize, δ(k), by utilizing one first order feedback average unit at time point k as represented as follows:
 
δ( k )=β*δ( k −1)+δ 0 *α( k )  (2)
 
   wherein β&lt;1 is the constant of the feedback average unit and is used to control the average length. δ 0  is a constant and is used to adjust the value of the correction coefficient α(k) so that the adaptive speech analysis unit  103  could adapt to the variation of the speech signals. Finally, the N&#39;th order adaptive prediction filter  23  produces the estimated value S e (k+1) for the next speech sample by combining the last N prediction samples and the estimated stepsize δ(k), as shown in the following equation: 
                 S   e     ⁡     (     k   +   1     )       =         ∑     i   =   0       N   -   1       ⁢         a   i     ⁡     (   k   )       *       S   e     ⁡     (     k   -   i     )           +     δ   ⁡     (   k   )                 (   3   )             
 
   Table 1 is the reference table of the adaptive stepsize decision unit  221 . The correction coefficient α(k) is determined according to this table. If the four consecutive bits are the same, it means that the S e (k) value estimated by the adaptive speech analysis unit  103  is not enough, so the correction coefficient α(k) is set to be 2, so that the adaptive speech analysis unit  103  could adapt to the variation of the voice sounds signals rapidly. If only three consecutive bits are the same, a smaller correction coefficient, α(k)=1, is given to slightly increase the stepsize. If any two successive bits of these four bits are different, the correction coefficient is reset as −1. This is because at this time the adaptive speech analysis unit  103  over estimates the speech signals and the stepsize is required to be decreased. For the other conditions, α(k)=0, which represents the status that the adaptive speech analysis unit  103  can adapt to the variation of the speech signals. 
     FIG. 3  is the circuit block diagram of the coefficients estimation of the adaptive prediction filter  23 , which is used to produce N coefficients of N&#39;th order, a i (k), i=1,2, . . . N. The block diagram of the adaptive prediction filter  23  comprises one hard limiter  31 , two rows of tapped delay lines with the length of N−1, one row of first order feedback average units with the length of N, a multiplier line of length N−1, and an amplifier. Two input signals include the speech signals estimated signal S e (k) and the digital bit b(k). First of all, the prediction S e (k) is sent into the hard limiter  31  to decide the sign of S e (k). The output of the hard limiter  31  is +1 or −1. Afterward, the last N hard-limited prediction values are stored in the delay line  1 . For b(k), it is amplified with a constant gain 0&lt;e&lt;1 and sent into delay line  2  to store the last N amplified bits. Finally, the estimated adaptive prediction filter coefficient a i (k), i=2,3, . . . N are generated with the multiplier line and the coefficients filter bank according to the following equation:
   a   i ( k )= d*a   i ( k −1)+ e*b ( k )*SGN[ S   e ( k )]  (4) 
   wherein d is a constant which represents the average length of the first order feedback average unit. The heuristic value of d is 0.9. SGN[ ] represents the operation of the hard limiter  31 . Basically, equation (4) represents a simplified stochastic gradient-based algorithm. It is noted that the generation of a 0 (k) is modified according to the following equation:
 
 a   0(   k )= d*a   0 ( k −1)+ e*b ( k )*SGN[ S   e ( k )]+ f   (5),
 
   where f&gt;0 is a constant and is used to emphasize the high correlation between the current speech sample and the latest one. 
     FIG. 4  is the circuit block diagram of the pitch detection unit, which is used to estimate the pitch periods of the speech signals. The pitch detection unit  105  comprises one row of tapped delay lines with the length of (P max −P min +1), the subtraction line with a length of (P max −P min +1), the absolute value line with a length of (P max−P   min +1), a pitch filter bank with a length of (P max−P   min   +1), and one pitch decision unit 41. P   max  represents the maximum possible pitch period of the voice sounds, and P min  represents the minimum possible pitch period of the voice sounds. If the sampling frequency is 32 KHz, then P max ≈320, P min ≈96 so that the length of the tapped delay lines, subtraction line, absolute value line, and the number of first order feedback average units is  225 . First of all, the input samples S nn (k)&#39;s are sent into the delay line to store the last (P max−P   min +1) values. The S nn (k)&#39;s are subtracted by its delayed versions at the subtraction line. Following that, the absolute values from the subtraction line are sent into a pitch filter bank to average the correlation between S nn (k)&#39;s and its delayed versions. The above-mentioned operation is to search the degree of correlation between S nn (k) and its proceeding samples. Assume the correlation between S nn (k) and S nn (k−P) is the highest, then the smallest value of the output of the pitch filter corresponds to the Pth delay unit. Therefore, in the pitch decision unit  41 , the desired pitch period P is detected according to the following equations: 
               P   =       arg       P   min     ≤           ⁢   i   ⁢           ≤           ⁢     P   max         ⁢     {     min   ⁡     (     E   ⁡     [              S   nn     ⁡     (   k   )       -       S   nn     ⁡     (     k   -   i     )              ]       )       }         ,     
     ⁢       if   ⁢           ⁢     min   ⁡     (     E   ⁡     [              S   nn     ⁡     (   k   )       -       S   nn     ⁡     (     k   -   i     )              ]       )         ≤     E   th               (   6   )                 P   =   0     ,       if   ⁢           ⁢     min   ⁡     (     E   ⁡     [              S   nn     ⁡     (   k   )       -       S   nn     ⁡     (     k   -   i     )              ]       )         &gt;     E   th               (   7   )               
   wherein E[ ] represents the operation of a first-order pitch filter and 
         arg       P   min     ≤           ⁢   i   ⁢           ≤           ⁢     P   max         ⁢     {     min   ⁡     (   |   )       }         
 
represents the selection of the parameter which makes the value within the bracket a minimum. E th  is a threshold value of the output value of the pitch filter which is one empirical value used to distinguish between vowel and non-vowel samples. If the current sample does not belong to the vowel in the voice sounds signals, the detected P=0.
 
     FIG. 5  is the circuit block diagram of the background noise suppression unit which is used to combine the speech signal characteristic coefficient a i (k) and the detected speech signal pitch period P obtained from the adaptive speech analysis unit and the speech signal pitch decision unit, respectively, to process the suppression of the background noise. The background noise suppression unit  104  comprises two rows of tapped delay lines with the length of N, one delay unit with the delay amount of P, an adder line with a length of N+1, one noise shaping filter  51 . The input signals are the speech signals S nn (k), the speech signal characteristic coefficient a l (k), and the speech signal period P. The output is the enhanced speech sample, Ŝ n (k). The first tapped delay line saves the previous N speech samples, which are Snn(k−1),Snn(k−2), . . . , and Snn(k−N). The second delay line also stores the last N speech samples, which is delayed beforehand for P samples according to the detected pitch period P, that is, Snn(k−P),Snn(k−P−1), . . . Snn(k−P−N). After that, these two groups of signals of Snn(k),Snn(k−1), . . . Snn(k−N) and Snn(k−P),Snn(k−P−1),Snn(k−P−N) are summed and sent into the noise shaping filter  51  along with the voice sounds speech signal characteristic coefficient a i (k). Since there is a high degree of similarity between the speech signals in these two signals, it is a harmonic addition for the speech signals, while the background noise does not have such a similarity. Therefore, it is a non-harmonic addition. Thus, the noise-suppression effect with harmonic addition can be achieved. At the noise shaping filter  51 , these N+1 combined samples are filtered according to the following transfer function: 
               H   ⁢           ⁢     (   z   )       =       1   -       ∑     j   =   1     N     ⁢       β   j     ⁢     a   j     ⁢     z     -   j               1   -       ∑     i   =   1     N     ⁢       α   i     ⁢     a   i     ⁢     z     -   i                       (   8   )               
   wherein α and β are two constants, 0≦β≦α≦1, and are used to control the shape of the signal spectrum. Since a i  represents the characteristics of the speech signals, the spectrum of the original signal will be transformed into the shape that is similar to that of the speech signals after the transformation of the noise shaping filter  51 . That is, the spectra of the background noise vary with the spectra of the speech signals. This is the so-called masking effect and the benefit of suppression of the background noise thus has been achieved. Since we have performed the harmonic addition beforehand, it elevates the result of the masking effect. 
   Next, the speech signals, after being processed by the background noise suppression unit  104 , are sent into the high-frequency booster  106 .
 
 H   f ( z )=1 −γz   −1   (9)
 
   Basically, this is a first order high pass filter, 0&lt;γ&lt;1, which is used to compensate for the influence of high frequency attenuation caused by the noise shaping filter. Finally, it passes through the low pass filter, which is the same as the proceeding one, to remove the noise outside the speech bandwidth. 
   The suppression system of background noise of speech signals and the method thereof of this invention has the following advantages in comparison with the above-mentioned cited inventions and other traditional technologies:
     1.This invention provides a suppression system of background noise of speech signals and the method thereof that utilizes one all pole linear prediction filter to re-build the model of speech signals. Also, it detects the pitch period which only exists in the speech signals. Finally, it suppresses the background noise according to the associated estimated speech signal coefficients and the pitch periods of the speech signals and further elevates the quality of the speech signals.   2. This invention provides a suppression system of background noise of voice sounds and the method thereof wherein the degree of its complexity is relatively low and it requires only one microphone, so it is very suitable to be used in mobile phone applications and the technology of speech recognition, to elevate the quality of speech coding and the recognition rate of the speech.   

   The above-mentioned detailed description of this invention is an explanation of one embodiment of this invention; however, said embodiment is not intended to limit the claims of this invention; all the equivalent practice or modification without departing from the spirit of this invention should be encompassed by the claims of this invention. Many changes and modifications in the above-mentioned embodiment of the invention can, of course, be carried out without departing from the scope thereof. 
   
     
       
             
           
             
             
             
             
             
           
             
             
             
             
             
           
         
             
               TABLE 1 
             
           
           
             
                 
             
             
               reference table of the adaptive stepsize decision unit 
             
           
        
         
             
               b(n) 
               b(n − 1) 
               b(n − 2) 
               b(n − 3) 
               a(n) 
             
             
                 
             
           
        
         
             
               −1 
               −1 
               −1 
               −1 
               2 
             
             
               1 
               1 
               1 
               1 
               2 
             
             
               −1 
               −1 
               −1 
               1 
               1 
             
             
               1 
               1 
               1 
               −1 
               1 
             
             
               −1 
               1 
               1 
               1 
               1 
             
             
               1 
               −1 
               −1 
               −1 
               1 
             
             
               1 
               1 
               −1 
               −1 
               0 
             
             
               −1 
               −1 
               1 
               1 
               0 
             
             
               −1 
               1 
               1 
               −1 
               0 
             
             
               1 
               −1 
               −1 
               1 
               0 
             
             
               −1 
               −1 
               1 
               1 
               0 
             
             
               1 
               1 
               −1 
               −1 
               0 
             
             
               1 
               −1 
               1 
               1 
               0 
             
             
               −1 
               1 
               −1 
               −1 
               0 
             
             
               −1 
               1 
               −1 
               1 
               −1 
             
             
               1 
               −1 
               1 
               −1 
               −1