Abstract:
An integrated circuit device includes a fast-locking phase locked loop (PLL). This PLL includes a phase-frequency detector and first and second charge pumps, which are responsive to first and second control signals generated by the phase-frequency detector. The first and second charge pumps have different current sourcing characteristics when the first control signal is active and different current sinking characteristics when the second control signal is active.

Description:
REFERENCE TO PRIORITY APPLICATION  
       [0001]     This application claims priority to Korean Patent Application No. 2004-57107, filed Jul. 22, 2004, the disclosures of which are hereby incorporated herein by reference.  
       FIELD OF THE INVENTION  
       [0002]     The present invention relates to phase locked loop integrated circuits and methods of operating same.  
       BACKGROUND OF THE INVENTION  
       [0003]     A PLL (Phase Locked Loop) is commonly used for communication, multimedia, and other applications.  FIG. 1  is a block diagram illustrating a conventional charge pump PLL (Phase Locked Loop). An input clock  101  is inputted to a pre-divider  110  and the pre-divider  110  converts the input clock  101  to a lower frequency clock  111 . The converted lower frequency clock  111  is provided to a phase frequency detector (PFD)  120 . The phase frequency detector  120  compares a phase of the lower frequency clock  111  to a phase of a final clock  161  generated from a main-divider  160  and outputs an UP signal  121  and/or a DOWN signal  122 . When the phase of the lower frequency clock  111  leads the phase of the final clock  161 , the UP  121  signal is activated and the DOWN signal  122  is inactivated. Conversely, when the phase of the lower frequency clock  111  lags behind the phase of the final clock  161 , the DOWN signal  122  is activated and the UP signal  121  is inactivated.  
         [0004]     A charge pump  130  outputs a current (Icp)  131  to a loop filter  140  when the UP signal  121  is activated and pulls the current (Icp)  131  from the loop filter  140  when the DOWN signal  122  is activated. An output voltage  141  of the loop filter  140  increases when the phase frequency detector  120  outputs the UP signal  121  having an active state, and the output voltage  141  of the loop filter  140  decreases when the phase frequency detector  120  outputs the DOWN signal  122  having an active state. The loop filter  140  is illustrated as containing a resistor R and capacitors C 1  and C 2 .  
         [0005]     The output voltage  141  of the loop filter  140  is provided to a voltage-controlled oscillator (VCO)  150  and is used for controlling a frequency of an output clock  151 . This output clock  151  may be the same signal as FOUT. The frequency of the output clock  151  outputted from the VCO  150  is generally proportional to an input voltage of the VCO  150  (i.e., the output voltage  141  of the loop filter  140 ). The output clock  151  of the VCO  150  is divided by the main-divider  160  and the divided output clock  161  is fed back to the phase frequency detector  120 . The main-divider  160  may be optionally included in the charge pump PLL. In particular, the output clock  151  of the VCO  150  is divided by the main-divider  160  and the divided output clock  161  is provided to the phase frequency detector  120  when the PLL performs a function of frequency multiplication. In addition, the main-divider  160  and the pre-divider  110  can determine a frequency ratio of the output clock  161  to the input clock  101 .  
         [0006]     An important factor in defining the performance of the PLL is a ‘locking time’ that represents a time required for generating an output clock synchronized to an input clock and having a predetermined target frequency. Communication, multimedia, and other applications utilizing the PLL require a fast locking time.  
         [0007]     Referring to the charge pump PLL shown in  FIG. 1 , the locking time may be re-defined as a time required for a control voltage  141  of the VCO  150  to reach a voltage level that is required to generate the predetermined target frequency. According to the conventional charge pump PLL shown in  FIG. 1 , the magnitude of the current (Icp)  131  outputted from the charge pump  130  during an initial stage of a phase lock operation is equal to the magnitude of the current (Icp)  131  outputted from the charge pump  130  during a stage in which the phase lock is almost completed. The locking time of the PLL is substantially inversely proportional to the quantity of the current (Icp)  131  outputted from the charge pump  130 . However, when the quantity of the current (Icp)  131  outputted from the charge pump  130  is increased in order to reduce the locking time of the charge pump PLL, spectral purity (or reliability) of the PLL is degraded and noise of the output clock increases. That is, in a PLL employing single charge pump, there is often a trade-off between fast locking time and good reliability.  
         [0008]     In order to solve these problems, a structure of a modified PLL is disclosed in Japan Patent No. 98376. The PLL of the Japan Patent No. 98376 includes a plurality of charge pump units and the PLL operates in two modes, i.e. a high-speed mode in which the charge pump units provide a large current and a low noise mode.  
         [0009]     However, the PLL of the Japan Patent No. 98376 controls the switching between the two modes of the charge pump unit, which provides a large current in the high-speed mode, using a logic circuit. The PLL can&#39;t variably control the quantity of the current outputted from a charge pump based on a phase difference between an input clock and an output clock. Additionally, jitter of the output clock may be generated since a switching noise due to a switching of the charge pump unit for performing the high-speed mode is applied to a loop filter.  
         [0010]     Another conventional charge pump PLL is disclosed in U.S. Pat. No. 5,424,689, which is entitled “Filtering device for use in a phase locked loop controller”. The charge pump PLL of U.S. Pat. No. 5,424,689 includes two-type charge pumps, including of a high current charge pump for providing a large current and a small current charge pump for providing a small current. However, the current transfer of two charge pumps are controlled using a variable transmission characteristic of a loop filter based on a fact that the transmission characteristics of the loop filter depend upon connect points between each of the two charge pumps and the loop filter.  
       SUMMARY OF THE INVENTION  
       [0011]     Integrated circuit devices according to embodiments of the invention include a phase locked loop (PLL). This PLL includes a phase-frequency detector and first and second charge pumps, which are each responsive to first and second control signals generated by the phase-frequency detector. The phase-frequency detector is responsive to first and second clock signals. The first and second charge pumps have different current sourcing characteristics when the first control signal is active and different current sinking characteristics when the second control signal is active. These different current sourcing characteristics support fast locking of the PLL. The PLL also includes a loop filter. This loop filter may have first and second input terminals and a voltage-controller oscillator electrically coupled to an output terminal of the loop filter. The first charge pump has an output electrically coupled to the first input terminal of the loop filter and the second charge pump has an output electrically coupled to the second input terminal of the loop filter.  
         [0012]     According to preferred aspects of these embodiments, the current sourcing characteristics of the second charge pump dominate those of the first charge pump when a phase difference between the first and second clock signals is greater than a first threshold. This first threshold, which relates directly to a pulse width of the first control signal, is typically exceeded when the PLL is initially enabled and the pulse width of the first control signal is large. Alternatively, the current sourcing characteristics of the first charge pump dominate those of the second charge pump when the phase difference between the first and second clock signals is less than the first threshold. This condition is typically present when the PLL is near a lock condition between the first and second clock signals and the pulse width of the first control signal is relatively small. 
     
    
     BRIEF DESCRIPTION OF THE DRAWINGS  
       [0013]      FIG. 1  is a block diagram illustrating a conventional charge pump PLL (Phase Locked Loop);  
         [0014]      FIG. 2  is a block diagram illustrating a charge pump PLL (Phase Locked Loop) according to an example embodiment of the present invention;  
         [0015]      FIG. 3  is a circuit diagram illustrating first and second charge pumps and a loop filter included in a PLL (Phase Locked Loop) according to an example embodiment of the present invention;  
         [0016]      FIGS. 4A through 4D  show signal waveforms during an initial stage of phase lock according to an example embodiment of the present invention;  
         [0017]      FIGS. 5A through 5C  show signal waveforms during a last stage of the phase lock according to an example embodiment of the present invention; and  
         [0018]      FIGS. 6A through 6B  show simulation waveforms of an output voltage of a loop filter according to an example embodiment of the present invention. 
     
    
     DETAILED DESCRIPTION OF THE INVENTION  
       [0019]     Detailed illustrative embodiments of the present invention are disclosed herein. However, specific structural and functional details disclosed herein are merely representative for purposes of describing example embodiments of the present invention. This invention may, however, be embodied in many alternate forms and should not be construed as limited to the embodiments set forth herein. Accordingly, while the invention is susceptible to various modifications and alternative forms, specific embodiments thereof are shown by way of example in the drawings and will herein be described in detail. It should be understood, however, that there is no intent to limit the invention to the particular forms disclosed, but on the contrary, the invention is to cover all modifications, equivalents, and alternatives falling within the spirit and scope of the invention. Like numbers refer to like elements throughout the description of the figures.  
         [0020]      FIG. 2  is a block diagram illustrating a charge pump PLL (Phase Locked Loop) according to an example embodiment of the present invention. An input clock (FIN)  201  is inputted to a pre-divider  210  and the pre-divider  210  converts the input clock  201  to a low frequency clock (FREF)  211 . The low frequency clock  211  is provided to a phase frequency detector  220 . The phase frequency detector  220  compares a phase of the low frequency clock  211  to a phase of a final clock (FFEED)  261  generated from a main-divider  260  and outputs an UP signal  221  and/or a DOWN signal  222 . When the phase of the low frequency clock  211  leads the phase of the final clock  261 , the UP  221  signal is activated and the DOWN signal  222  is inactivated. Conversely, when the phase of the low frequency clock  211  lags behind the phase of the final clock  261 , the DOWN signal  222  is activated and the UP signal  221  is inactivated.  
         [0021]     A charge pump  230  outputs currents to a loop filter  240  or pulls currents from the loop filter  240  through two paths  231  and  232 . In particular, a current is outputted to the loop filter  240  through the first path  231  or is pulled from the loop filter  240  through the first path  231  based on the states of the UP signal  221  and the DOWN signal  222 . In contrast, the second path  232  controls the quantity of the current, which is outputted to the loop filter  240  or pulled from the loop filter  240 , in proportion to a phase difference between the input clock  211  and the output clock  261 .  
         [0022]     The loop filter includes resistors R 1  and R 2  and capacitors C 1  and C 2 . The output voltage  241  of the loop filter  240  is provided to a voltage controlled oscillator (VCO)  250  and is used for controlling a frequency of an output clock  251 , which may be equivalent to the signal FOUT. The output clock  251  of the VCO  250  is divided by the main-divider  260  and then the divided output clock  261  is fed back to the phase frequency detector  220 . The inclusion of a main-divider  260  is optional.  
         [0023]      FIG. 3  is a circuit diagram illustrating first and second charge pumps and a loop filter included in a fast locking charge pump PLL (Phase Locked Loop) according to an example embodiment of the present invention. The fast locking charge pump PLL shown in  FIG. 3  according to an example embodiment of the present invention includes a first charge pump  350  and a second charge pump  300 . The first charge pump  350  pushes (or pulls) a current provided from current sources  355  and  356  to/from the loop filter  360  via a first current path  357  using a first switch  353  and a second switch  354 . The first switch  353  and the second switch  354  operate in response to the UP signal  221  and the DOWN signal  222  outputted from the phase frequency detector  220 .  
         [0024]     Features of the second charge pump  300  will now be described. An exclusive OR gate  305  included in the second charge pump  300  receives the UP signal  221  and the DOWN signal  222  outputted from the phase frequency detector  220 , and the result of the logic operation and an enable signal (EN)  303  are provided to an AND gate  306 . The enable signal (EN)  303  is used for determining whether the second charge pump  300  is enabled or not. The second charge pump  300  can operate based on the UP signal  221  and the DOWN signal  222  when the enable signal  303  is activated. When both of the UP signal  221  and the DOWN signal  222  are in an inactive state (e.g., a logic low level), the output of the AND gate  306  has an inactive state. When the UP signal  221  is in an active state and the DOWN signal  222  is in an inactive state or when the UP signal  221  is in an inactive state and the DOWN signal  222  is in an active state, the output of the AND gate  306  has an active state (e.g., a logic high level). In addition, because both the UP signal  221  and the DOWN signal  222  are in an active state during a reset operation of the phase frequency detector  210 , the exclusive-OR gate  305  disregards this condition by providing a logic 0 signal to the AND gate  306 .  
         [0025]     A second current path  347  of the second charge pump  300  is coupled to serially coupled resistors  361  and  362  included in the loop filter  360 . In alternative embodiments, the loop filter  360  may have various configurations depending upon filtering characteristics of the loop filter, however, in the illustrated embodiment of the present invention, the loop filter  360  includes a first capacitor  363  coupled between an output terminal  365  of the loop filter  360  and the ground, a second capacitor  364  serially coupled to the resistors  361  and  362  as shown in  FIG. 3 .  
         [0026]     An operation of the second charge pump  300  is now described below with reference to  FIGS. 3, 4A  through  4 D and  5 A through  5 C.  FIGS. 4A through 4D  show signal waveforms during an initial stage of phase lock according to an example embodiment of the present invention. In the initial stage of phase lock of  FIG. 4A through 4D , the phase difference between the input clock and the output clock is typically very large.  FIGS. 5A through 5C  show signal waveforms during a last stage of phase lock according to an example embodiment of the present invention. In the last stage of phase lock of  FIG. 5A through 5C , the phase difference between the input clock and the output clock is typically small.  
         [0027]     The charge pump PLL according to an embodiment of the present invention adaptively operates based on a phase difference between an input clock and an output clock.  
         [0028]     With reference to  FIGS. 4A through 4D , there is explained the first operation in the case where the phase difference of the input clock and the output clock is large during the initial stage of phase lock and, at the same time, a phase of the input clock leads a phase of the output clock.  FIG. 4A  is waveform showing the UP signal  221  and the DOWN signal  222  outputted from the phase frequency detector  220  in the above-mentioned condition. As shown in  FIG. 4A , the UP signal in an active state has wide width and the DOWN signal is in an inactive state. The output of the AND gate  306  has an inactive state during a first section  402  where the UP signal is in an inactive state and the DOWN signal  222  has an inactive state. When this occurs, the PMOS transistor  310  is turned-on and a fast locking up voltage (hereinafter referred to as “FLU” voltage)  343  is pre-charged to a high power supply voltage VDD. The FLU voltage  343  is applied to a control electrode of a PMOS transistor  335  and then used for controlling the turn-on intensity of the PMOS transistor  335 . In addition, a diode coupled NMOS transistor  337 , which is serially coupled to the PMOS transistor  335 , is controlled by a fast locking down voltage (hereinafter referred to as “FLD” voltage)  344 . The FLD voltage  344  has a symmetrical waveform with respect to the waveform of the FLU voltage  343 .  
         [0029]      FIG. 4B  illustrates waveforms showing variations of the FLU voltage  343  and the FLD voltage  344  according to a state transition of the UP signal  221 . After the FLU voltage  343  is pre-charged to the high power supply voltage VDD in response to the inactive state of the UP signal  221 , when the UP signal  221  goes to an active state ( 401 ) from an inactive state ( 402 ), a switch  341  is closed in response to the active state of the UP signal  221 . Meanwhile, when the UP signal  221  goes to the active state ( 401 ), the output of the AND gate  306  goes to an active state. In response, the NMOS transistor  320  is turned-on. As a result, a predetermined current is provided through a current source  325  and a bias capacitor  330 , and then the FLU voltage  343  decreases during the period  401 . While the FLU voltage  343  decreases, a PMOS transistor  336  is turned-on. In response, a current is outputted from the high power supply voltage VDD to the loop filter  360  through the second current path  347 .  
         [0030]      FIG. 4C  is waveform showing a current ICP 1  provided to the loop filter  360  from a current source  355  in the first charge pump  350  in response to the UP signal  221 .  FIG. 4D  is waveform showing a current ICP 2 , which is controlled by the PMOS transistor  336  based on the FLU voltage  343  to be provided to the loop filter  360 . The current ICP 1  outputted from the first charge pump  350  shown in  FIG. 4C  and the current ICP 2  outputted from the second charge pump  300  shown in  FIG. 4D  are provided to the loop filter  360  together. Generally, the second charge pump  300  outputs a relatively high current ICP 2  compared with the current ICP 1  outputted from the first current sources  355  and  356  of the first charge pump  350 . Thus, the second charge pump  300  can reduce the locking time. In the example embodiments of the present invention, the current quantity of the second current source  325  included in the second charge pump  300  is about two to three times as large as the current quantity of the first current sources  355  and  356  included in the first charge pump  350 .  
         [0031]     There is now explained the second operation in case the phase difference between the input clock and the output clock is large during the initial stage of phase lock and, at the same time, a phase of the output clock leads a phase of the input clock. The second operation, in which the UP signal  221  is inactivated and the DOWN signal  222  is activated, may be easily understood with reference to the symmetrical relationship between the FLU voltage  343  and the FLD voltage  344  as shown in  FIG. 4B . While the DOWN signal  222  is in an inactive state, the FLU voltage  343  is pre-charged to the high power supply voltage VDD and PMOS transistor  335  is off and the FLD voltage  344  goes to the ground voltage level. Conversely, while the DOWN signal  222  is in active state, the FLU voltage  343  decreases and a level of the FLD voltage  344  increases in symmetrical relationship with the FLU voltage  343 . As the FLD voltage  344  increases, an NMOS transistor  338  is turned-on and then pulls a current from the loop filter  360  via the second current path  347 . Because the first charge pump  350  and the second charge pump  300  pull a relatively large current from the loop filter  360 , a voltage level of the output terminal  365  in the loop filter  360  rapidly decreases in a similar way as the case when a phase of the input clock leads a phase of the output clock.  
         [0032]     Hereinafter, there is explained operations for the case where a phase difference of the input clock and the output clock is small during a last stage of phase lock with reference to  FIGS. 5A through 5C . First, a third operation for the case where a phase of the input clock leads a phase of the output clock will be explained.  FIG. 5A  is waveform showing the UP signal  221  and the DOWN signal  222  outputted from the phase frequency detector  220  in the above-mentioned condition. As shown in  FIG. 5A , the UP signal  221  in an active state has narrow width compared with the UP signal  221  shown in  FIG. 4A , and the DOWN signal  222  is in an inactive state. During the period  502  while the UP signal is in an inactive state, an output of the AND gate  306  has an inactive state. Thus, the PMOS transistor  310  is turned-on and the FLU voltage  343  is pre-charged to the high power voltage VDD. The FLU voltage  343  is applied to a control electrode of a PMOS transistor  335 , and then is used for controlling the turn-on intensity of the PMOS transistor  335 .  
         [0033]     In addition, a diode coupled NMOS transistor  337 , which is serially coupled to the PMOS transistor  335 , is controlled by the FLD voltage  344 . The FLD voltage  344  has a symmetrical waveform with respect to the waveform of the FLU voltage  343  as shown in  FIG. 5B .  
         [0034]      FIG. 5B  shows variations of the FLU voltage  343  and the FLD voltage  344  according to state transition of the UP signal  221 . After the FLU voltage  343  is pre-charged to the high power supply voltage VDD in response to the inactive state of the UP signal  221 , when the UP signal  221  goes to an active state from an inactive state, a switch  341  is closed in response to the UP signal  221 .  
         [0035]     Meanwhile, the output of the AND gate  306  goes to an active state when the UP signal  221  goes to an active state, and then an NMOS transistor  320  is turned-on. As a result, a current is provided through a current source  325  and a bias capacitor  330 , and then the FLU voltage  343  decreases. While the FLU voltage  343  decreases, the PMOS transistor  336  remains turned-on. Thus, a current is outputted from the high power supply voltage VDD to the loop filter  360  through the second current path  347 . However, the UP signal  221  is changed to an inactive state from an active state before the voltage level of the FLU voltage  343  completely drops. This is because the period  501  where the UP signal  221  is in an active state has a narrow width. Consequently, the PMOS transistor  336  is turned-off right after the PMOS transistor  336  is weakly turned-on.  
         [0036]      FIG. 5C  is waveform showing current quantity provided to the loop filter  360  from a second charge pump  300 . As shown in  FIG. 5C , the second charge pump  300  provides a relatively low level current to the loop filter  360  compared with the current provided from the second charge pump  300  shown in  FIG. 4D   
         [0037]     There is now explained a fourth operation for the case where a phase difference between the input clock and the output clock is small during a last stage of the phase lock and, at the same time, a phase of the output clock leads a phase of the input clock. The fourth operation may be easily understood with reference to the symmetrical relationship between the FLU voltage  343  and the FLD voltage  344  as shown in  FIG. 5B . In the fourth operation, the UP signal  221  is inactivated and the DOWN signal  222  is activated. While the DOWN signal  222  is in an inactive state, the FLU voltage  343  is pre-charged to the high power supply voltage VDD, and the FLD voltage  344  is discharged to the ground voltage. Conversely, while the DOWN signal  222  is in active state, the FLU voltage  343  decreases since a current is provided through the current source  325  and the bias capacitor  330 . As a result, a level of the FLD voltage  344  increases in symmetrical relationship with the FLU voltage  343 . Accordingly, as the FLD voltage  344  increases, the NMOS transistor  338  is turned-on, and then a current is pulled from the loop filter  360  via the second current path  347 . In such case, however, the DOWN signal  222  is changed to an inactive state from an inactive state before the FLD voltage  344  completely (or fully) rises since the period where the DOWN signal  222  is in an active state has a narrow width. Consequently, the NMOS transistor  338  is turned-off right after the NMOS transistor  338  is weakly turned-on. That is, the charge pump  300  pulls a relatively low current from the loop filter  360 .  
         [0038]     As described above, the second charge pump  300  can control the quantity of current that is provided to the loop filter or is provided from the loop filter by increasing or by decreasing the FLU voltage  343  and the FLD voltage  344  based on the pulse width of the UP signal  221  and the DOWN signal  222  and the bias capacitor  330 .  
         [0039]     In order to suitably control the quantity of the current, the threshold voltages of the current switching elements PMOS transistor  336  and the NMOS transistor  338  included in the second charge pump  300  may be adjusted. For example, the threshold voltage of the PMOS transistor  336  may be set to a value ((VDD−VSS)×⅔+VSS). VDD denotes a high power voltage, and VSS denotes a low power voltage. VSS may have a negative voltage or a ground level. The threshold voltage of the NMOS transistor  338  may be set to a value ((VDD−VSS)×⅓+VSS).  FIGS. 6A and 6B  show waveforms of an output voltage of a loop filter according to an example embodiment of the present invention. In detail,  FIGS. 6A and 6B  show a voltage-time graph that indicates improved locking time of the fast locking charge pump PLL according to an example embodiment of the present invention. As mentioned above, the locking time may be defined as a time required before a control voltage of the VCO  150  is maintained at a fixed voltage level.  
         [0040]      FIG. 6A  is a simulation waveform showing a locking time measured while the enable signal EN is activated.  FIG. 6B  is a simulation waveform showing a locking time measure while the enable signal EN is inactivated. As shown in  FIGS. 6A and 6B , in order to generate a predetermined target frequency, the control voltage of the VCO is set to the level of about 0.78 volts. As shown in  FIG. 6A , the measured locking time Ta is about 463 milliseconds, and as shown in  FIG. 6B , the measured locking time is about 688 milliseconds.  
         [0041]     Therefore, the proposed fast locking charge pump PLL according to embodiments of the present invention can reduce the locking time up to about 32.7% in comparison with the locking time of the conventional charge pump PLL.  
         [0042]     According to the example embodiments of the present invention, the quantity of the current outputted from the charge pump is controlled based on the phase difference between the phase of the input clock and the phase of the output clock. In an initial stage of the phase lock, a large current is provided to the loop filter or is provided from the loop filter. In a last stage of the phase lock, a small current is provided to the loop filter or is provided from the loop filter. Thus, the locking time may be reduced.  
         [0043]     While the example embodiments of the present invention and their advantages have been described in detail, it should be understood that various changes, substitutions and alterations may be made herein without departing from the scope of the invention.