Abstract:
A converter powered by an alternating network drawing therefrom a current with a power factor close to unity and a non-linear distortion factor close to five percent, wherein the amplitude of the current applied to an output load remains substantially constant. A bridge circuit is provided using switches and capacitors wherein the reactance at the quench frequency is selected such that a portion of the converted energy is added between the terminals of an output capacitor to the main current rectified by a bridge. A buffer source has a direct voltage with substantially constant amplitude which enables balancing of the generated voltages, thereby eliminating the risk of destruction by uncontrollable excess voltages.

Description:
BACKGROUND OF THE INVENTION 
     1. Field of the Invention 
     The present invention relates to electronic converters referred to as “self-compensated” electronic converters which are connected to the AC line voltage and provide at an output a high-frequency signal of substantially constant amplitude, while the AC line current remains substantially sinusoidal and in phase with the voltage because of the energy transfer mode recovery of a suitable portion of the previously converted high-frequency energy. 
     2. Description of the Related Art 
     The prior art system of this kind which offers the best performance is shown in the accompanying FIG. 1, which shows the most beneficial embodiment of the system claimed in U.S. Pat. No. 5,134,556. In that embodiment, which is representative of the prior art, the output terminal B of the converter A delivers the high-frequency converted energy via a galvanic isolation capacitor C whose capacitance is chosen so that its impedance at said high frequency does not significantly interfere with the resonant frequency of the output oscillatory circuit, which include&#39;s the inductor D, the output load E and the phase-shifter capacitor F. Unlike the capacitor C, the capacitor F must have an impedance at the high switching frequency such that the amplitude of the alternating current signal developed between its terminals reaches a chosen value. That signal, applied to one of the non-polarized input terminals of the rectifier bridge I, enables the envelope of a low-frequency rectified signal to be recovered between the terminals of the capacitor H. 
     The polarized outputs of the rectifier bridge I are connected in series with the polarized outputs of the AC line voltage rectifier bridge J, with the result that said low-frequency envelope between the terminals of the capacitor H is added to the rectified AC line voltage signal, which improves the power factor of the AC line current. 
    
    
     BRIEF DESCRIPTION OF THE SEVERAL VIEWS OF THE DRAWINGS 
     Further to FIG. 1 relating to the prior art, 
     FIG. 2 illustrates a general embodiment of the self-compensating converter of the invention; 
     FIG. 3 illustrates a first embodiment of the self-compensating converter of the invention shown in FIG. 2; 
     FIG. 4 illustrates a second embodiment of the self-compensating converter of the invention shown in FIG. 2; 
     FIG. 5 illustrates a third embodiment of the self-compensating converter of the invention shown in FIG. 2; and 
     FIG. 6 illustrates a final embodiment of the self-compensating converter of the invention shown in FIG.  2 . 
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     By recovering a portion of the high-frequency converted energy in this way, in proportion to the current flowing in the output load E, the power factor of the AC line current can only be compensated in a very approximate manner and there is no real reduction of its harmonic content. 
     For this reason, it is therefore necessary to use an additional circuit for adding to said signal proportional to the current flowing in the output load E a second rectified signal proportional to the high-frequency voltage between the terminals of the output load E. 
     That circuit includes the capacitor G whose impedance is chosen in accordance with said high frequency and delivers a voltage signal of suitable amplitude at the non-polarized second input terminal of the rectifier bridge I. 
     After rectification, a new low-frequency envelope is then available between the terminals of the capacitor H, where it is added to the previously recovered current envelope. 
     Only the addition of these three envelopes enables a system of this kind to comply with standards concerning the AC line current. 
     Despite its high energy efficiency and its apparent simplicity, a system of the above kind has a number of drawbacks, as mentioned hereinafter. 
     1) The necessity to adjust precisely the respective amplitudes of the current and voltage envelopes recovered in this way between the terminals of the capacitor H. 
     2) The necessity to use an additional protection device which must be capable of absorbing transient overvoltages that could develop between the terminals of the capacitor H, especially when the voltage is applied to the converter A, and whose energy can in some cases lead to immediate destruction of the converter. 
     The system in accordance with the invention alleviates the above drawbacks and, with very simple means, achieves a power factor of the AC line current which is close to unity, combined with a total harmonic distortion (THD) of that current of around 5%, a value which is currently far from being complied with by the most sophisticated prior art systems. 
     The accompanying FIG. 2 shows a general embodiment of the system in accordance with the present invention. 
     The system includes a high-frequency self-oscillator using a structure referred to as a “capacitor half-bridge” which is fed with direct current from polarized common terminals  8   a  and  8   b  shunted by a decoupling capacitor  8 . 
     The active arm of the bridge converter includes switching means 1′ and 1″ connected in series. 
     The terminals at the outside ends of the resulting series circuit are connected to terminals  8   a  and  8   b , respectively. 
     The passive arm of the bridge converter includes the capacitors  3   a  and  3   b , which are also connected in series. 
     The terminals at the outside ends of the resulting series circuit are connected to the terminals  8   a  and  8   b , respectively. 
     The output load  2  which is to receive the high-frequency converted energy is connected between the midpoint  1  of said active arm and the midpoint  3  of said passive arm. 
     Thus, as soon as a DC voltage of sufficient amplitude is applied between the terminals  8   a  and  8   b  and a control device, not shown, sustains alternating cyclic conduction of the switching means 1′ and 1″, a high-frequency switching current can flow through the load  2  in a circuit which is closed by the capacitors  3   a  and  3   b  whose reactance at said high frequency is calculated so that the AC voltage developed between the midpoint  3  and either terminal  8   a  or  8   b  is a non-zero voltage with a chosen amplitude. 
     The high-frequency AC voltage developed in this way between the midpoint  3  and one of the polarized common terminals is then fed via the buffer DC voltage source  4  to the non-polarized input terminal  5  of the full-wave rectifier bridge including the diodes  5   a  and  5   b.    
     This is possible because the impedance of the buffer DC voltage source  4  to the high-frequency alternating current generated in this way is negligible, even though the DC voltage of virtually constant amplitude between terminals  3  and  5  can be of considerable magnitude. 
     The polarized output circuit of said doubler bridge, which is shunted by the decoupling capacitor  5 , after it has been appropriately oriented, is connected in series with the polarized output circuit of the AC line voltage rectifier bridge  7  whose non-polarized input terminals  7   a  and  7   b  are connected to the AC line voltage. 
     As soon as voltage is applied to the terminals  7   a  and  7   b,  the rectified AC line current can charge the decoupling capacitor  8  via the suitably polarized diodes  5   a  and  5   b.    
     As soon as alternate cyclic conduction of the switching means 1′ and 1″ has been established, a high-frequency alternating current flows through the output load  2 . 
     The predetermined fraction of this current which cannot flow through the capacitors  3   a  and  3   b  because of their reactance at said high frequency loads the input terminal  5  of said doubler bridge via the buffer DC voltage source  4 . 
     After this current is rectified, a low-frequency envelope is recovered between the terminals of the decoupling capacitor  6 . Its amplitude is proportional to the high-frequency current flowing through the load  2 . 
     This low-frequency envelope is then added to the low-frequency envelope derived from the rectified AC line current between the terminals  7   c  and  8   b.    
     Although the maximum amplitudes of these two low-frequency envelopes necessarily have a large relative phase difference, those amplitudes nevertheless remain proportional to each other. 
     This is because the envelope derived from the rectified AC line current is, ignoring losses, proportional to the converted energy absorbed by the output load  2 . 
     Moreover, the amplitude of the high-frequency AC voltage that is applied to the terminal  5  is also proportional to the converted energy. 
     The amplitude of the low-frequency envelope between the terminals of the capacitor  6 , after rectification, therefore also remains proportional to the low-frequency envelope derived from the rectified AC line current. 
     If the low-frequency envelope corresponding to the rectified high-frequency current recovered in this way has a suitable amplitude, merely adding it to the signal corresponding to the rectified AC line current between the terminals of the capacitor  6  is sufficient to correct virtually all of the effects that the high capacitance of the capacitor  8  might have on the linearity of the AC line current. 
     The only constraint that must imperatively be complied with to obtain optimum results from this system is restricted to providing a buffer source  4  which has a negligible impedance to said high-frequency alternating current and delivers a DC voltage V 3  free of spurious low-frequency modulation. 
     The value of the voltage V 3  is directly related to the value of the DC voltage V 2  developed between the midpoint  1  and one of the common terminals  8   a  or  8   b  and the value of the DC voltage V 4  developed between the terminal  5  and the common terminal  8   b.    
     That value can be approximately calculated using the equation 
     
       
           V   3 ≈( V   2 − V   4 ). 
       
     
     To make the example more concrete, it is assumed that the decoupling capacitor  8  is charged to a DC voltage V 1  of 370 V, for example. 
     As V 1 ≈2×V 2 , the voltage V 2  is then substantially equal to 370 V÷2, i.e. approximately 185 V. 
     The DC voltage V 5  between the terminals  7   c  and  8   b  is therefore approximately 160 V. 
     As V 5 ≈V 4 ×2, the DC voltage developed between the terminals  5  and  8   b  is substantially equal to 160 V÷2, i.e. approximately 80 V. 
     The mean DC voltage V 3  to be maintained between the terminals  3  and  5  of the buffer source  4  is therefore 185 V−80 V, ice. approximately 105 V. 
     By observing this simple rule, it is possible to obtain perfect adaptation of the system in accordance with the invention and, with no additional circuitry, to achieve quasi-perfect correction of the power factor and the harmonic distortion of the AC line current. 
     Constructed as described above, and without requiring any particular adjustment, this system typically achieves a power factor of 0.995 for the AC line current and a total harmonic distortion of 7%, and the voltage between the common terminals  8   a  and  8   b  is subject to only negligible modulation. 
     The low modulation of the voltage between the common terminals  8   a  and  8   b  results in low modulation of the envelope of the high-frequency current flowing through the output load  2  and a very small amplitude of the current flowing through the capacitor  8 . 
     The accompanying FIG. 3 shows a practical embodiment of the present invention, which is distinguished from the previous one as indicated hereinafter. 
     This embodiment of the system in accordance with the invention uses a capacitor half-bridge converter whose active arm includes the series-connected transistors  1   a  and  1   b , or other semiconductors adapted to serve as switching means, and whose passive arm includes the series-connected capacitors  3   a  and  3   b  , which have a given reactance to said high-frequency alternating current. 
     The primary  9   a  is connected between the midpoints  1  and  3  of these bridge arms and, by virtue of being coupled to the magnetic circuit  9 , is substituted for said output load  2 . 
     Alternate cyclic conduction of the transistors  1   a  and  1   b , controlled by the secondaries  9   b  and  9   c  which are appropriately oriented and coupled to the magnetic circuit  9 . 
     To assure alternate cyclic conduction therein, said secondaries apply a signal of appropriate amplitude and phase to the control junction of the transistors  1   a  and  1   b , respectively, via limiter resistors  11   a  and  11   b.    
     The recovery high-frequency AC voltage developed between the terminal  3  and either polarized common terminal  8   a  or  8   b  is fed via the appropriately polarized high-value capacitor  15  to the non-polarized input terminal of the doubler rectifier bridge including the appropriately polarized diodes  5   a  and  5   b.    
     As before, the polarized output terminals  7   c  and  8   b  of said rectifier bridge are shunted by the filter capacitor. 
     The recovered high-frequency current rectified in this way takes the form of a low-frequency envelope which, after it is added to the envelope corresponding to the AC line current rectified by the rectifier bridge  7 , as mentioned above, compensates the AC line current from the non-polarized input terminals  7   a  and  7   b.    
     The appropriately polarized diodes  10   a  and  10   b  respectively connected in anti-parallel with the transistors  1   a  and l b  assure the dual flow of current between the midpoint  1  and either polarized common terminal  8   a  or  8   b.    
     After voltage is applied to the system, cyclic conduction of the resulting converter is initiated conventionally by the trigger device combining the resistor  14   a,  the capacitor  14   d,  the inhibitor diode  14   b  and the voltage threshold device  14   c.  The control electrode of the transistor  1   b  is therefore excited by a suitable signal. 
     The winding  9   d  coupled to the magnetic circuit  9  therefore delivers the converted energy to the receiver  12  connected between its terminals, in a mode referred to as “voltage transfer”. 
     The capacitor  13  connected in parallel with the receiver  12  has the following functions. 
     Firstly, if the magnetic circuit  9  is designed to have the smallest possible air gap, the function of the capacitor  13  is to limit the effects of the leakage inductance affecting the resulting transformer. 
     Secondly, if the magnetic circuit  9  intentionally has a large air gap, the function of the capacitor  13  is to constitute, with the inductance of the secondary  9   d , a parallel resonant circuit whose overvoltage effects can be exploited in the power supply of the receiver  12 . 
     In this arrangement, the rectified AC line voltage between the polarized output terminals  8   a  and  7   c  of the rectifier bridge  7  is automatically applied to the high-value capacitor  15  which provides said buffer DC voltage source  4 . 
     This is because the capacitor  15  can be charged via the series circuit including the transistor  1   a,  the primary  9   a,  the resistor  15   a  which limits the initial charging overcurrent and the diode  5   a  which maintains the voltage between the terminals  3  and  5  at a constant value corresponding to said voltage V 3 . 
     The DC voltage between the terminals  3  and  5  is therefore affected by low-frequency ripple whose level depends essentially on the continuous charge that the capacitor  15  can accumulate. 
     It is therefore advantageous for the capacitor  15  to have the highest possible capacitance. 
     The capacitor must transmit the rectified AC line voltage envelope without attenuating it. 
     In ordinary low-power applications, the ripple on the DC voltage V 3  between the terminals  3  and  5  remains virtually negligible if the capacitor  15  has a value of several tens of microfarads. 
     Concomitantly, the impedance of a capacitor of this value to the recovered high-frequency current flowing from the terminal  1  to the terminal  5  also remains negligible. 
     The high-value capacitor  15  then behaves as a buffer DC voltage source whose quasi-constant amplitude enables adaptation of the various potentials developed within a system of this kind. 
     The capacitor  15  therefore fulfils perfectly the function of said buffer DC voltage source  4 . 
     Constructed in this way, the system of the invention achieves excellent compensation of the power factor of the AC line current and an extremely low level of harmonics therein. 
     Moreover, the low-frequency ripple affecting the DC voltage between the common terminals  8   a  and  8   b  is maintained at a very low level, which in the final analysis leads to low ripple on the high-frequency current envelope applied to the receiver  12  and a small excursion of the amplitude of the current with low-frequency ripple flowing through the capacitor  8 . 
     The accompanying FIG. 4 shows another embodiment of the system in accordance with the invention. 
     In accordance with what has been described hereinabove, this embodiment differs from the preceding one as follows: 
     Firstly, the inductance of the primary  9   a  constitutes, with the capacitor  16  connected in series with it, a series oscillatory circuit in which resonance occurs at a frequency close to that of alternate cyclic conduction of the transistors  1   a  and  1   b.    
     In this system, the high-frequency converted energy is extracted in the mode referred to as “energy transfer”. 
     This is because, in this embodiment, the receiver  12  is connected directly between the terminals of the capacitor  16  and is therefore exposed to the high-frequency AC potential developed between its terminals. 
     Connected in this way, the receiver diverts a suitable portion of the high-frequency current flowing between the terminal  1  and the terminal  3 . 
     The converted energy portion applied in this way to the receiver  12 , whose impedance is known, is then limited to a suitable value that is determined by the impedance of the primary  9   a  and the reactance of the capacitor  16 . 
     Precise adjustment of the amplitude in this way is easily obtained by a judicious choice of the values of these two components. 
     The function of the resistor  17  shunting the receiver  12  and the capacitor  16  is to pass the direct current required to charge the capacitor  15  if said receiver includes a dielectric barrier. 
     In this case, the resistor  17  could equally be connected between the terminal  8   a  and the terminal  3 , which would enable continuous charging of the capacitor  15 , as before. 
     This resistor could be replaced by the resistor bridge  17   a  and  17   b  which is connected between the common terminals  8   a  and  8   b  and whose midpoint is connected to the terminal  3 . 
     The capacitor  15  serving as the buffer DC voltage source  4  could also be charged at a constant voltage to a substantially constant amplitude in this way. 
     The suitably polarized diode  18  shunting the capacitor  15  is optional and its function is to improve the transmission of the high-frequency alternating current flowing between the terminals  3  and  5 . 
     Because of this diode, the capacitor  15  carries only one half-wave of said high-frequency recovered current. 
     The accompanying FIG. 5 shows another embodiment of the system in accordance with the invention. 
     This embodiment differs from the previous ones in that an additional inductor  19  is connected in series with the capacitor  16  to form a series oscillatory circuit therewith. 
     In this case, the impedance of the primary  9   a  makes no significant contribution to the resonant frequency of said oscillatory circuit since, associated with the secondaries  9   b  and  9   c , this primary has no function other than to constitute an independent transformer which controls alternate cyclic conduction of the transistors  1   a  and  1   b.    
     In this embodiment the capacitors  3   a  and  3   b  are replaced by a single capacitor  3   c  whose capacitance is twice that of each of those two capacitors. 
     The reactance of the single capacitor at said high frequency therefore remains substantially the same as the resultant of the other two capacitances, which achieves similar performance while saving one component. 
     Here, as indicated above, the resistor  17  enables charging of the voltage reservoir capacitor  15  from the terminals  8   a  and  7   c  by circumventing possible galvanic isolation or non-linear characteristics of the output receiver  12 . 
     The resistor  15   a  for limiting the inrush current when voltage is applied to the AC line voltage input terminals  7   a  and  7   b  to charge the voltage reservoir capacitor  15  is connected in series with the transistors  1   a  and  1   b  constituting said active bridge arm. 
     The accompanying FIG. 6 shows a final embodiment of the system in accordance with the invention. 
     This embodiment differs from the embodiment shown in the accompanying FIG. 2 in that the voltage reservoir capacitor  15  serving as the buffer DC voltage source  4  is no longer connected between the terminals  3  and  5 , but instead between the terminals  1  and  3 , in series with the output load  2 . 
     In this case, the terminal  3  and the terminal  5  are connected together. 
     The low-value resistor  15   a  connected in series with the capacitor  15  limits the inrush current when voltage is applied. 
     Before said converter is started up and the switching means 1″ begin to conduct, the high-value resistor  17   c  connected between the terminal  8   a  and the terminal  1  pre-charges the capacitor  15  to a DC voltage and compensates the self-discharge due to the leakage current that is inevitable with any capacitor. 
     As previously described, the high-value resistor  17  closes the direct current charging circuit to the voltage reservoir capacitor  15  if the output load  2  has isolation or galvanic discontinuity characteristics corresponding to a negative or non-linear resistance, for example. 
     In this embodiment, as in the preceding ones, for a converted power from 10 W to 50 W the crucial components could have the following values, for example: 
     
       
         
               
               
               
             
           
               
                   
                   
               
             
             
               
                   
                  8 
                 10 μF/350 V electrolytic capacitor 
               
               
                   
                 15 
                 47 μF/100 V electrolytic capacitor 
               
               
                   
                 15a 
                 10 ohms/0.25 W resistor 
               
               
                   
                 17/17c 
                 470 kilohms/0.25 W resistor 
               
               
                   
                   
               
             
          
         
       
     
     The rectified AC line voltage available between the polarized output terminals  8   a  and  7   c  of the rectifier bridge  7  therefore charges the capacitor  15  to a stable DC voltage with practically no residual ripple at 100 Hz or 120 Hz, because the discharge current of the high-capacitor connected in this way is negligible. 
     Because the high-value storage capacitor  15  has only a very low impedance at the low frequency of the rectified AC line voltage, the high-frequency converted alternating current which flows through it is practically free of any modulation at 100 Hz or 120 Hz. 
     This feature essentially distinguishes the function of the capacitor  15 , used as a non-modulatable buffer DC voltage source, from the function of the capacitor C in the accompanying FIG. 1, which is merely to provide a galvanic barrier, between whose terminals the high-frequency converted current is modulated at 100 Hz or 120 Hz with an amplitude which can be equal to that of the rectified AC line voltage between the output terminals of the diode bridge J. 
     The system in accordance with the invention as just described assures virtually perfect correction of the power factor and harmonic distortion of the AC line current. 
     This result is obtained by adding to said rectified AC line current envelope only a low-frequency envelope resulting from rectification of a given portion of the high frequency energy, unlike the approach adopted in prior art systems in which, to achieve a less good result, it is necessary to add two separate low-frequency envelopes obtained by rectifying a current signal and a voltage signal, both of which are derived from the high-frequency converted energy. 
     What is more, unlike the system shown in the accompanying FIG. 1, the system in accordance with the invention eliminates dangerous overvoltages between the terminals of the capacitors  8  and  6  to which the capacitors H and K are subjected and whose principal cause is highly excessive overmodulation of the converted current at 100 Hz or 120 Hz. 
     The system in accordance with the invention, which is simple to construct and requires no fastidious adjustments, corrects the drawbacks of prior art systems. 
     The system of the invention can be used with advantage in all low-cost applications which must comply with standards concerning the AC line current, such as AC line voltage power supplies, electronic transformers, electronic ballasts, compact fluorescent lamps, etc. As emerges from the foregoing description, and as is obvious in any event, the invention is in no way limited to the embodiments that have been specifically described, and to the contrary encompasses all variants thereof.