Abstract:
A flat plate array is provided which permits generation of two independent beams from a single slotted waveguide antenna. The two beams are coincident in space, but are of two different linear polarizations, those polarizations being orthogonal, i.e., at right angles to each other. In the preferred embodiment, a plurality of slots are provided in a flat top plate of a waveguide cavity. The slots are located in rows and columns with a predetermined spacing between pairs of slots positioned in the respective rows and columns. Each beam is associated with its own input/output port and either the rows or columns of slots of the array. Coupling the two ports with a suitable power splitter and phase shifter permits the antenna to produce a single beam with any elliptical polarization, any linear polarization, right circular polarization, or left circular polarization, plus a second coincident beam with polarization characteristics &#34;orthogonal&#34; to the first, for example, right circular polarization and left circular polarization.

Description:
BACKGROUND OF THE INVENTION 
     This invention relates to a slot array radiator, and more particularly, to a dual input/output port, dual polarization flat plate slot array antenna. 
     There long has been a need for an efficient, compact, flat antenna capable of generating coincident broadside beams with orthogonal polarizations, or a single beam whose polarization may be fully adjusted. It is well known that radar targets, for example, reflect different amounts of energy back to a radar receiver depending upon the polarization of the incident beam. The ability to readily change the polarizations from a single slotted planar array antenna greatly increases the capability of a radar detector. A radar detector employing the antenna of this invention is able to make the desired polarization change easily during target detection. 
     Slotted waveguide flat plate antennas are well known in the art. Such antennas also have been proposed for dual polarization and arbitrary polarization modes. In the past, the designs proposed have been handicapped by a number of design deficiencies. Previous to my invention, offered designs required the slots of such a flat plate array antenna to be positioned one waveguide wavelength apart. With such spacing, prior art antennas had low efficiencies for broadside beams because of the large gaps in the aperture, and so called &#34;grating&#34; lobes or &#34;second order&#34; beams resulted. The antenna disclosed hereinafter permits the slots to be placed one-half waveguide wavelength apart, thereby &#34;filling&#34; the aperture and eliminating grating lobes and obtaining higher aperture efficiency for broadside beams. In addition, as disclosed hereinafter, size of the antenna of this invention may be varied merely by altering the waveguide mode number, the numbers of rows and columns of slots, and adjusting the size of the top plate and the waveguide cavity. The prior art references of which I am aware include U.S. Pat. No. 3,599,216 (&#39;216), which shows a circular polarized planar array antenna having alternately displaced transverse slots over virtual walls for one component, and a set of conventional shunt slots between virtual walls for the other component of a circularized polarized beam. The &#39;216 patent, however, deals with a single port, single beam, fixed single circular polarization slotted waveguide broadside pencil beam antenna. 
     U.S. Pat. Nos. 3,623,112 and 4,063,248 and 4,353,072 all describe radiating elements which involve a combination of waveguide radiators and dipole radiators, the latter having coax and/or stripline feeding which limits RF power handling. Each functions in a manner substantially different from the invention disclosed hereinafter. 
     U.S. Pat. Nos. 2,982,960 and 3,281,851 and 3,348,227 and 3,503,073 show approaches that require full waveguide wavelength spacing between at least some of the radiating slots to achieve a broadside beam. That type of construction is a flaw if off-broadside second order beams are to be suppressed without using heavy and lossy dielectric loading in the waveguides. 
     U.S. Pat. Nos. 3,382,501 and 3,340,534 show a single port, single sense of circular polarization radiators formed by adding wire loops external to slots or open ended waveguides. 
     U.S. Pat. No. 4,197,541 shows a square coaxial transmission line radiator with coaxial line network elements which make the device unsuitable for use at millimeter wavelengths. 
     U.S. Pat. No. 4,266,228 shows ordinary cross slots on rectangular waveguides, which, as previously indicated, requires that the slot spacing be one waveguide wavelength apart in order to produce a broadside beam and would have second order beams under that condition. 
     The invention disclosed hereinafter provides a means to obtain two independent beams from a single slotted waveguide antenna. It does so with a compact &#34;flat plate&#34; design which is simple to manufacture. As will be appreciated by those skilled in the art, the fact that all of the slots are in a single slotted plate allows the use of precise photolithographic techniques, especially useful with millimeter wavelengths designs. 
     One of the objects of this invention is to provide a dual polarization slot antenna array with an independent terminal for each polarization. 
     Another object of this invention is to provide a dual polarization slot array antenna in which the slots of the radiating element may be positioned one-half waveguide wavelength apart, yet have the slots radiate in phase. 
     Another object of this invention is to provide a simplified antenna structure. 
     Another object of this invention is to provide an antenna structure which permit elliptical polarizations, linear polarizations, and circular polarizations from a single antenna structure. 
     Another object of this invention is to provide a single antenna structure which permits transmission on right circular polarization and receive on left circular polarization, or transmission on any desired polarization and receive on any different polarization. 
     Another object of this invention is to provide ease of fabrication for flat plate antennas regardless of how high a microwave frequency of operation is required. 
     Another object of this invention is to provide an antenna with lower resistive losses than obtained in flat plate antennas formed of a multiplicity of individual rectangular waveguides, each rectangular waveguide having slot radiators. 
     Another object of this invention is to allow the transmission of high microwave power levels without RF power breakdown, particularly for millimeter wavelengths. 
     Another object of this invention is to provide an antenna for passive &#34;listen-only&#34; systems for analysis of the polarization characteristics of received signals. 
     Other objects of this invention will be apparent to those skilled in the art in light of the following description and accompanying drawings. 
     SUMMARY OF THE INVENTION 
     In accordance with this invention, generally stated, a dual polarization flat plate antenna is provided which permits generation of two independent beams from a single slotted antenna area. The two beams are coincident in space, but of two different polarizations. Two linear polarizations are provided at right angles to one another. That is to say, the polarizations are orthogonal. In the preferred embodiment, a first set of slots are provided in respective rows and columns, all slots being parallel to one another. That first set forms a broadside antenna beam as a result of coupling between that first set of slots and one waveguide mode in the region under the slotted plate. A second set of slots, all perpendicular to the first set of slots, form a second broadside beam as a result of those slots coupling to a second waveguide mode. The two coincident beams are differentiated by their polarizations and by each beam having its own terminal or input/output port. Since all slot spacings, in either set, are well under a free space wavelength, second order beams and grating lobes are eliminated. 
    
    
     BRIEF DESCRIPTION OF THE DRAWING 
     In the drawings, 
     FIG. 1 is top plan view of one illustrative embodiment of the slot array antenna of this invention; 
     FIG. 2 is a sectional view taken along the line 2--2 of FIG. 1; 
     FIG. 3 is a bottom plan view of the array shown in FIG. 1; 
     FIG. 4 is an enlarged diagrammatic view, partly broken away, taken about the area 4--4 of FIG. 1; 
     FIG. 4A is an enlarged diagrammatic view, partly broken away, corresponding to FIG. 4, but illustrating a second embodiment of this invention; 
     FIG. 4B is an enlarged diagrammatic view, partly broken away, corresponding to FIG. 4, but illustrating a third embodiment of this invention; 
     FIG. 4C is a sectional view partly broken away, taken along the line C--C of FIG. 4B; 
     FIG. 5 is one illustrative measurement of an E-plane pattern obtained with the antenna of this invention; and 
     FIG. 6 is one illustrative measurement of an H-plane pattern obtained with the antenna of this invention. 
    
    
     DESCRIPTION OF THE PREFERRED EMBODIMENT 
     Referring now to the FIG. 1, reference numeral 1 indicates one illustrative embodiment of array of this invention. Array 1 includes a top plate 2, a bottom plate 3, a first pair of oppositely opposed side walls 4 and 5, respectively, and a second pair of oppositely opposed side walls 6 and 7. 
     The top, bottom and sides define a cavity 8 which is designed to support the rectangular waveguide mode TE P ,N propagating left-right in FIG. 1, and a TE Q ,N mode propagating up-down in FIG. 1. The notations &#34;P&#34; and &#34;Q&#34; are non-zero integers and may be equal or unequal. In the symbols TE P ,N and TE Q ,N, TE refers to the electric field of the mode, P, the mode number, represents the number of maxima of the electric field along one direction, and N represents the number of maxima along a direction perpendicular to the one direction, and Q, the mode number, represents the number of maxima of the electric field along a predetermined direction perpendicular to the one direction and N represents the number of maxima along a direction perpendicular to the predetermine direction. For the purpose of this specification and the embodiment illustrated, &#34;P&#34; and &#34;Q&#34; were arbitrarily selected as an integer 10. Those skilled in the art will recognize that the principles described hereinafter apply regardless of the integer chosen for &#34;P&#34; and &#34;Q&#34; and that the size of the antenna and the number of radiating slots will change with changes in &#34;P&#34; and/or &#34;Q&#34;. The references to rectangular waveguide modes correspond to the mode descriptions contained in the book entitled Waveguide Handbook, edited by N. Marcuvitz, published by McGraw-Hill Book Company, Inc., 1951, pages 55-66. The invention would work as well if TE P ,N and TE Q ,N modes were used with &#34;N&#34; being an integer other than zero but N=0 will be used throughout the description hereafter. 
     Each of the sides 4, 5, 6, and 7 have a waveguide connection indicated generally by the numeral 9. The connections 9 are utilized to attach the antenna to a suitable feed network, generally indicated by the reference numeral 100 in FIG. 3. Those skilled in the art will recognize that a wide variety of waveguide, coax, or stipline feed networks may be employed with the array of this invention. 
     While described as &#34;sides&#34;, as shown in FIG. 2 each of the sides 4, 5, 6, and 7 are themselves rectangular waveguides. The sides or waveguides 4 and 5 are shown in cross section in FIG. 2, while the side or waveguide 6 is shown in side view. The waveguides may be mounted as shown in FIG. 2, or rotated 90°. Waveguide 6 has a plurality of feed slots 10 formed in it. The number of feed slots 10 in each of the sides 4, 5, 6, and 7 correspond to the value of &#34;P&#34; for sides 4 and 5, and to &#34;Q&#34; for sides 6 and 7. For the purpose of this description, there are ten slots in each &#34;side&#34;. The top plate 2 has a plurality of radiating slots 11 formed in it. 
     The length dimension of the cavity 8 is a constant for a given microwave frequency of operation. In the preferred embodiment, the cavity 8 size is related to the values of P and Q. If the bottom wall or floor of the cavity is arbitrarily taken to be the starting measuring point and &#34;N&#34; is zero, then the distance to the top of the cavity 8 must be well under one-half of a free space wavelength, λ, at the microwave frequency of interest. Referring to FIG. 1, if equal spacing between the radiating slots 11 for each of the two beams is desired, then the left-right or X dimension of the cavity is chosen to be Qλ/√2 and the up-down or Y dimension is chosen as Pλ/√2. Equal X direction and Y direction spacing is not a requirement for array operation. Ten slots are visible in the XZ plane of FIG. 2, and there are a like number of slots not visible in FIG. 2 in the side 7 end of the cavity and facing the visible set. As previously indicated, P and Q may be arbitrarily chosen. There is a similar set of feed slots in the sides 5 and 4. The P plus P slots of the sides 4 and 5 are feed slots to excite the TE P ,O rectangular waveguide mode when the slots are properly excited. For purposes of this specification, the TE P ,O mode is chosen to propagate in the plus/minus X direction of a conventional cartesian coordinate system, sometimes referred hereinafter as the X-TE P ,O to indicate propagation direction, referenced with respect to FIG. 1. As indicated, there are Q slots in each of the rectangular feed guides 6 and 7. These Q plus Q slots are feed slots to excite the TE Q ,O mode which propagates in the plus/minus Y direction of a conventional cartesian coordinate system, sometimes referred to hereinafter as the Y-TE Q ,O mode. 
     The essence of this invention is the discovery of a means to independently excite both the TE P ,N waveguide mode propagating in the X direction, and the TE Q ,N waveguide mode propagating in the Y direction, then being able to have one set of slots couple only to one mode and a second set of slots couple only to the other mode. 
     The means for exciting the modes has already been partially described. There are a number of extant methods for exciting the needed modes, known in the art, and a detailed description is not repeated here for description simplicity. FIG. 4 shows a few of the radiating slots 11 in the top plate 2. The electric currents in the inside surface of the top plate 2 are shown as a series of dotted lines with arrow points for the T Q ,O mode and a series of solid lines with arrow points for the T P ,O mode in FIG. 4. The arrow points show the instantaneous directions of currents. For the first embodiment to be described, each plurality of slots 15, i.e., each in-line group of radiating slots with their long dimension parallel to the Y direction, shall be excited by the TE P ,O mode which propagates in the plus/minus X direction. If slots S1, S2, S3 and S4 were equally spaced from each other, each of those slots would intercept TE P ,O mode solid line currents with one end of the slot interrupting currents in one direction while the other end of the slot interrupts equal magnitude currents flowing in the opposite direction. Under those conditions there is no net excitation of the slots. 
     In fact, slots S1 and S2 are positioned close to each other with their ends a distance D1 apart so that slots S1 and S2 intercept more of the solid line currents directed to the right in FIG. 4. Slots S3 and S4 are also moved to make their ends D1 apart so that they too intercept more right-directed current than current flowing to the left. The adjacent ends of S2 and S3 thus become far apart, at a distance of D2. Slots S5 through S8 are one-half a waveguide wavelength away from S1 through S4 and thus the waves there are π radians or 180 degrees out of phase with the waves at the first location. 
     Since all radiating slots must be in phase to create the desired broadside beam, the displacements of slots S5 through S8 are opposite the displacements of S1 through S4 in order to have all slots in phase. Note that by moving the first two slots S5 and S6 away from each other, those slots are moved into the domain of the right directed solid line currents thus making their radiation in phase with S1 and S2. Similarly for S7 and S8. Now, the smaller D1 spacing is between the central two slots. This process is carried out over the entire aperture to cause all radiating slots to be in phase despite the half waveguide wavelength spacing of slots in the propagation direction. This technique was employed in the &#39;216 patent discussed above. 
     It is the discovery of the technique for having a second mode orthogonal to the first and yet selectively avoid coupling to that second mode that is the essence of this invention. 
     The TE Q ,O mode propagating in the Y direction causes the dotted line currents on the inside of the top plate 2 of FIG. 4. In order for a slot to be excited and radiate, there must be a component of current flow perpendicular to the long dimension of the slot. Inspection of FIG. 4 shows that the dotted line currents of the Y-TE Q ,O mode are all parallel to the long dimension of slots S1 and S8 and all other slots of slot set 15. So, the TE Q ,O waveguide mode does not couple to any of the vertical slots of the slot set 15. 
     Excitation of a horizontal slot set 25 by the currents of the TE Q ,O mode is accomplished in exactly the manner described for the vertical slots, except that it is the TE Q ,O mode that is exciting the slot set 25. The alternating spacing of the horizontal slots so as to always interrupt the upward directed currents of the TE Q ,O mode puts all of the horizontal slots&#39; radiation in phase by the same mechanism described for the other set of slots. 
     As thus described, it may be seen that the slot set 15 is arranged in a plurality of &#34;P-1&#34; rows and &#34;Q&#34; columns in which the slots are arranged vertically, in which the slot set 25 is arranged in a plurality of &#34;P&#34; rows and &#34;Q-1&#34; columns in which the slots are arranged horizontally, referenced to FIGS. 1 and 4. Individual ones of pairs of slots of the slot sets 15 and 25 are separated by the distance D1, which pairs of the slots of the sets 15 and 25 are separated by the distance D2. 
     FIG. 4A shows a second embodiment in which all of the slots are equally spaced from each other, unlike the situation in FIG. 4. As explained above, the slots won&#39;t couple when the slots are uniformly spaced because equal and opposite currents are interrupted by each slot for one mode, and the slots are parallel to the currents for the other mode. In FIG. 4A, a plurality of probes or posts 17 are added to each slot to perturb the fields in a manner familiar to those skilled in the art. Now, the vertically directed slots will couple only to the Y-TE Q ,N mode and the horizontally directed slots couple only to the X-TE P ,N mode. This is a reversal of the situation described for FIG. 4. The probes 17 are very slender posts attached only to the top plate 2 and projecting into the waveguide perpendicular to the top plate 2, and of a length to obtain the desired coupling of energy. The alteration of the side on which the probe is placed makes all slots of a given set radiate in phase. Other types of perturbing elements can be used instead of the slender cylindrical posts. 
     Alternatively, the perturbing posts can be attached only to the bottom plate 3 and protrude into the waveguide at the center of the length of each slot but alternating their offset from the slots in the same manner as indicated in FIG. 4A. 
     In either case, the probes or posts 17 couple only one set of slots to only one of the modes because the probes are located at an E-field zero, or virtual wall, of one of the modes and at the E-field maxima for that mode which gets coupled to one set of slots. 
     Finally, FIG. 4B shows another embodiment in which the slots are all equally spaced as in FIG. 4A. In the embodiment of FIG. 4B the coupling of the slots is accomplished by magnetic field coupling loops 18, instead of electric field probes or posts 17. The slots are made to be in phase by alternating the connection points of the coupling loops as shown in FIG. 4B and the side view of FIG. 4B shown in FIG. 4C. 
     In exciting the modes in the cavity 8, the opposing sets of feed slots in the cavity are joined by one magic T for one mode, and the other opposing set of feed slots adjoined by a second magic T. The unused port of each magic T has a short circuit so positioned as to create a short circuit at the &#34;side walls&#34; of the orthogonal mode. 
     Having used WR-90 waveguide in the slotted feed lines for convenience, it follows that a 1.8 inch waveguide wavelength was required to operate the 9 inch wide cavity in the TE mode in the preferred embodiment of this invention. Those figures lead to a theoretical operating frequency of 9273 MHz. 
     FIG. 5 is a measured E-plane pattern via the correct port for that polarization. The noise level trace results when the test detector is placed in the port for the orthogonal polarization, all other factors being unchanged. Approximately 30 dB isolation was obtained, but the exact value was unknown because the lower trace is in the noise level. 
     FIG. 6 is the H-plane pattern that goes with the E-plane pattern of FIG. 5. The near noise level trace results when the incident polarization is rotated 90°, all other factors remaining unchanged. 
     Unlike the various dual polarization antennas based upon the use of radial waveguides, the rectangular waveguide design of the present invention permits placement of elements one-half waveguide wavelength apart in the mode propagation direction, instead of a full wavelength apart, while permitting attainment of truly in phase radiation from all slots. The filled aperture of this rectangular waveguide design gives markedly improved aperture efficiency by eliminating second order beams. Those skilled in the art will appreciate that varying the amount of slot offsets from the lines of zero current allows for aperture tapering in the E-plane. Presently known radial waveguide slot antennas do not provide adequate means for varying the coupling between the waveguide and the exterior. 
     An alternative configuration for exciting the two orthogonal modes in the waveguides uses a single row of slots in the bottom of the cavity to excite the Y-TE P ,O mode and a second single row of slots, at right angles to the first row, to excite the X-TE Q ,O mode in the waveguide. This method requires that the configuration of the cavity walls in the XZ plane, the YZ plane, the plane Y=(P)(λ/√2) and in the plane X=(Q)(λ/√2) be such that those walls present a short circuit to the mode propagating parallel to any of those walls, and present an open circuit the mode propagating perpendicular to any of those walls. One method for achieving such characteristic for the walls is to use slots in a network identical to that described above for exciting the X-TE P ,O and X-TE Q ,O modes. In this later case, however, both ports of the magic T are shorted, with the shorts positioned to obtain the required zero and infinite impedence conditions at the side and end walls. 
     As thus shown and described, an orthogonal dual linear polarization array has a port associated with each polarization, and the linear polarizations are orthogonal. By combining the two ports through a suitable power divider and phase shifter network, any linear, elliptical or any circular polarization is obtained readily with complete variability to any point on the polarization sphere. By connecting the two ports via 90° phase shift 3 dB coupler, the antenna becomes an orthogonal dual circular polarization antenna, LHCP and RHCP. 
     Antenna size may be increased by increasing the mode index from TE 10 ,O to TE P ,O with P as large as desired. Conversely, the antenna size may be reduced by making P smaller than 10. Furthermore, the array need not be square. The array can be made rectangular by utilizing a TE P ,O mode in one direction, and a TE Q ,O mode in the orthogonal direction, P and Q being unequal non-zero integers. 
     Numerous variations, within the scope of the appended claims, will be apparent to those skilled in the art in light of the foregoing description and accompanying drawings. As indicated, the size and shape of the array may be varied in other embodiments of this invention. While certain design criteria are indicated as preferred, other criteria may be utilized if desired. Materials utilized in constructing the various components of the array 1 may be varied in embodiments of this invention. The array may be used with a great number of other associated circuits in addition to those described above. These variations are merely illustrative.