Semiconductor switch driving circuit

Abstract: To provide a semiconductor switch driving circuit in which stable continuity and disconnection can be kept, the high-speed switching operation is enabled, a lag of switching timing is minimized and which has a simple circuit, the semiconductor switch driving circuit for driving a semiconductor switch in which multistage switching devices (IGBT) are connected includes a transformer, a primary side and a secondary side and is configured so that voltage between the gate and the emitter of a switching device can be continuously kept positive, voltage between the gate and the emitter can be continuously kept negative, voltage between the gate and the emitter is alternately switched to positive voltage or negative voltage at high speed and can be kept.

Description: The present invention relates to a semiconductor switch driving circuit, particularly relates to a semiconductor switch driving circuit suitable for controlling a semiconductor switch used for electrotherapy apparatus such as a defibrillator. For a device for a semiconductor switch which enables the control of high voltage, an insulated gate bipolar transistor (IGBT) is generally used. A circuit for driving a semiconductor switch configured by this insulated gate bipolar transistor (hereinafter called IGBT) is connected via a photocoupler or a transformer so that the circuit is electrically insulated from a circuit part that directly drives a control signal and the gate of IGBT. Referring to drawings, an example using a photocoupler and an example using a pulse transformer respectively of a conventional type semiconductor switch driving circuit will be described below. Fig. 3 is a circuit diagram showing a semiconductor switch driving circuit using a photocoupler. As shown in Fig. 3, a part that drives a switching device (IGBT) 208a at a first stage is composed of a photocoupler 201a, a comparator 202a, a positive voltage source 203a, transistors 204a and 205a, a negative voltage source 206a and a resistor 207a and a ground terminal is connected to a GND1. Also, a part that drives a switching device (IGBT) 208b at a second stage is composed of a photocoupler 201b, a comparator 202b, a positive voltage source 203b, transistors 204b and 205b, a negative voltage source 206b and a resistor 207b, a ground terminal is connected to a GND2 and a driving circuit at the next stage or at the subsequent stages can be similarly composed. Fig. 4 is a circuit diagram showing a semiconductor switch driving circuit using a pulse transformer. As shown in Fig. 4, a part that drives a switching device (IGBT) 257a at a first stage connected to a secondary side of a pulse transformer 251 is composed of a transistor 255a, diodes 252a and 253a and resistors 254a and 256a, a part that drives a switching device (IGBT) 257b at a second stage is composed of a transistor 255b, diodes 252b and 253b and resistors 254b and 256b and a driving circuit at the next stage or the subsequent stages can be similarly composed. However, the conventional type semiconductor switch driving circuit has the following problems. The semiconductor switch driving circuit shown in Fig. 3 is provided with the photocoupler, the positive voltage source, the negative voltage source and the GND at every stage of a driven switching device (IGBT). In a conventional type system of a multistage semiconductor switch, there is a problem of a time lag in the switching of a switching device (IGBT). When the timing of the switching is delayed, overvoltage is applied to a switching device in case switching devices are connected in series as shown in FIG. 3, also, in case switching devices are connected in parallel, over current is applied to a switching device and in any case, the switching device may be broken. Also, as the same number of the photocouplers, the positive voltage sources, the negative voltage sources and the grounds as the number of the stages of the switching devices (IGBT) are required, there is a problem that the scale of the circuit is large and the cost of the whole apparatus is high. Also, the semiconductor switch driving circuit shown in FIG. 4 cannot continuously supply positive voltage or negative voltage to the gate of the switching device (IGBT) to be driven. There is also a problem that switching to reverse bias (from positive voltage to negative voltage or from negative voltage to positive voltage) is slow. US-A-5 939 927 discloses a semiconductor switch driving circuit used within a defibrillator and having a transformer, a primary side area provided on the primary side of the transformer for controlling current on the primary side of the transformer according to a control signal for controlling a semiconductor switch and a secondary side area provided on the secondary side of the transformer for driving a switching device such as a IGBT via a depletion mode transistor the drain of which is connected with the gate of the power transistor IGBT. The depletion mode transistor is in its normal state conducting and is controlled via the transformer by the control signal as supplied to the primary side area of the transformer in order to be cut off whereby the gate of the power transistor is charged to a positive voltage whereas in the absence of the control signal at the primary side area the depletion transistor is turned on and the gate voltage of the power transistor becomes zero volt. US-A-5 781 040 discloses a driver for a power transistor or IGBT using a transformer to isolate the power supply from the control signal. The control signal is one of two frequencies, and the isolated side of the driver includes a circuit for detecting which of the two frequencies is present. The output of the frequency detection circuit switches between low and high states depending on the frequency present, and the output of this circuit is connected to the input of the transistor driver circuit which charges the gate of the power transistor. Also this prior art circuit is capable of supplying only positive voltage to the gate of the power transistor, but is not capable of supplying negative voltage because the potential of a power supply provided in the isolated circuits is kept positive with regard to a source potential of the power transistor. Therefore, the gate-source voltage of the power transistor must be either one of zero or positive voltage in accordance with the state of a transistor provided to supply control current or voltage to the gate of the power transistor. It is the object of the present invention to provide a semiconductor switch driving circuit suitable for controlling a semiconductor switch which can continuously supply positive voltage or negative voltage to the gate of a switching device (IGBT) to be driven by the small number of parts, enables high-speed switching to reverse bias and is particularly used for electrotherapy apparatus because a lag in switching timing between each stage can be reduced. This object is solved by the features as claimed in claim 1. Further developments of the invention are claimed in sub-claims 2 to 10. A semiconductor switch driving circuit according to a the invention is capable of providing and maintaining the voltage between the gate and the source of the switching device or power transistor positive, negative or switched alternatively between positive and negative. According to a further development of the invention, when the primary side area receives an input control signal, it transmits power for controlling plural switching devices to a secondary side area and absorbs back electromotive force caused when current flowing in the transformer is cut off because a control signal input terminal is connected to the base of an NPN bipolar transistor via a resistor and a capacitor respectively connected in parallel, the base and the emitter of the NPN bipolar transistor are connected via a resistor, the emitter is connected to a ground terminal, the collector of the NPN bipolar transistor is connected to the gate of a P-channel MOSFET via a resistor, the gate and the source of the P-channel MOSFET are connected via a resistor, the source is connected to a power terminal, the drain of the P-channel MOSFET is connected to the anode of a diode, the cathode of the diode is connected to the drain of a N-channel MOSFET and a terminal of a primary winding of a transformer, the gate and the source of the N-channel MOSFET are connected via a resistor, the source is connected to a ground terminal, a control signal input terminal is connected to the gate of the N-channel MOSFET via a resistor, a control signal input terminal is connected to the base of an NPN bipolar transistor via a resistor and a capacitor respectively connected in parallel, the base and the emitter of the NPN bipolar transistor are connected via a resistor, the emitter is connected to a ground terminal, the collector of the NPN bipolar transistor is connected to the gate of a P-channel MOSFET via a resistor, the gate and the source of the P-channel MOSFET are connected via a resistor, the source is connected to a power terminal, the drain of the P-channel MOSFET is connected to the anode of a diode, the cathode of the diode is connected to the drain of a N-channel MOSFET and a terminal of the primary winding of the transformer, the gate and the source of the N-channel MOSFET are connected via a resistor, the source is connected to a ground terminal, a control signal input terminal is connected to the gate of the N-channel MOSFET via a resistor, terminals of the primary winding of the transformer are connected to a center tap, the center tap is connected to a power terminal and the center tap is connected to a ground terminal via a capacitor. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a circuit diagram showing a semiconductor switch driving circuit according to the invention; Figs. 2 (a) to (c) are timing charts showing each operation of the semiconductor switch driving circuit according to the invention; Fig. 3 is a circuit diagram showing a conventional type semiconductor switch driving circuit using a photocoupler; and Fig. 4 is a circuit diagram showing a conventional type semiconductor switch driving circuit using a pulse transformer. DETAILED DESCRIPTION OF PREFERRED EMBODIMENT Referring to the drawings, an embodiment of a semiconductor switch driving circuit according to the invention will be described in detail below. Fig. 1 is a circuit diagram for explaining an embodiment of the semiconductor switch driving circuit according to the invention. As shown in Fig. 1, a semiconductor switch driving circuit 100 for driving a semiconductor switch in which multistage switching devices (IGBT) are connected is composed of a transformer 103, its primary side area 101 and its secondary side area 102. The primary side area 101 is composed as follows. A control input terminal (for a signal PL) is connected to the base of an NPN bipolar transistor 108 via a resistor 105 and a capacitor 104 respectively connected in parallel, the base and the emitter of the NPN bipolar transistor 108 are connected via a resistor 106 and are connected to a ground terminal GND. The collector of the NPN bipolar transistor 108 is connected to the gate of a P channel MOSFET 110 via a resistor 107, the gate and the source of the P channel MOSFET 110 are connected via a resistor 109 and are connected to a power terminal VDD. The drain of the P channel MOSFET 110 is connected to the anode of a diode 111 and the cathode of the diode 111 is connected to the drain of a N channel MOSFET 114 and a terminal 127a of a primary winding of the transformer 103. The gate and the source of the N channel MOSFET 114 are connected via a resistor 113 and are connected to a ground terminal GND. A control input terminal (for a signal N) is connected to the gate of the N channel MOSFET 114 via a resistor 112. A control input terminal (for a signal NL) is connected to the base of an NPN bipolar transistor 120 via a resistor 117 and a capacitor 116 respectively connected in parallel, and the base and the emitter of the NPN bipolar transistor 120 are connected via a resistor 118 and are connected to a ground terminal GND. The collector of the NPN bipolar transistor 120 is connected to the gate of a P channel MOSFET 122 via a resistor 119, the gate and the source of the P channel MOSFET 122 are connected via a resistor 121 and are connected to a power terminal VDD. The drain of the P channel MOSFET 122 is connected to the anode of a diode 123 and the cathode of the diode 123 is connected to the drain of a N channel MOSFET 126 and a terminal 127d of the primary winding of the transformer 103. The gate and the source of the N channel MOSFET 126 are connected via a resistor 125 and are connected to a ground terminal GND. A control input terminal (for a signal P) is connected to the gate of the N channel MOSFET 126 via a resistor 124. Terminals 127b and 127c of the primary winding of the transformer 103 are connected to a center tap 135, further, the center tap 135 is connected to a power terminal VDD and is connected to a ground terminal GND via a capacitor 115. The secondary side area 102 is composed as follows. The emitter of a switching device (IGBT) 133a at a first stage and the collector of a switching device (IGBT) 133b at a second stage are connected, in case there are switching devices (IGBT) at stages following the second stage though they are not shown, they are similarly connected and multistage switching devices (IGBT) are connected in series. Gate driving sections 136a and 136b for directly controlling voltage between the gate and the emitter of each switching device (IGBT) are respectively composed as follows. In the gate driving section 136a, the anode of a (first) Zener diode 128a is connected to a terminal 127e at one end of a secondary winding of the transformer 103 and the cathode of a (second) Zener diode 129a is directly connected to the cathode of the (first) Zener diode 128a in series with both cathodes face to face and the anode of the (second) Zener diode 129a is connected to the gate of the switching device (IGBT) 133a via a (first) resistor 132a, a terminal 127f at the other end of the secondary winding is connected to the emitter of the switching device (IGBT) 133a, and a (second) resistor 130a and a capacitor 131a are connected between the anode of the (second) Zener diode 129a and the emitter of the switching device (IGBT) 133a. In the gate driving section 136b, the anode of a (first) Zener diode 128b is connected to a terminal 127g at one end of the second winding of the transformer 103 and the cathode of a (second) Zener diode 129b is directly connected to the cathode of the (first) Zener diode 128b in series with the cathodes face to face and the anode of the (second) Zener diode 129b is connected to the gate of the switching device (IGBT) 133b via a (first) resistor 132b, a terminal 127h at the other end of the secondary winding is connected to the emitter of the switching device (IGBT) 133b, and a (second) resistor 130b and a capacitor 131b are connected between the anode of the (second) Zener diode 129b and the emitter of the switching device (IGBT) 133b. Though not shown, in case there are gate driving sections at stages following the second stage, they are similarly composed. Next, the function of each side will be described. In the primary side area 101 of the semiconductor switch driving circuit, a control signal is input to transmit power for controlling plural switching devices (IGBT) 133a and 133b to the secondary side area 102 of the semiconductor switch driving circuit. Also, the primary side absorbs back electromotive force caused when current flowing in the primary winding of the transformer 103 is cut off. The secondary side area 102 of the semiconductor switch driving circuit receives power supplied from the primary side area 101 of the semiconductor switch driving circuit and transmits power for controlling the plural switching devices (IGBT) 133a and 133b to the plural switching devices (IGBT) 133a and 133b. These switching devices (IGBT) 133a and 133b at each stage receive the power supplied to the secondary side area 102 and cause or prevent current for switching 134 to flow. Further, the function of each circuit component will be described below. The capacitor 104 speeds up turning on/turning off the bipolar transistor 108. The resistor 105 limits the base current of the bipolar transistor 108. The resistor 106 equalizes the base potential of the bipolar transistor 108 to the potential of the emitter. The resistor 107 limits the collector current of the bipolar transistor 108. The bipolar transistor 108 executes the on-off control of the P channel MOSFET 110. The resistor 109 equalizes the gate potential of the P channel MOSFET 110 to the potential of the source. The P channel MOSFET 110 suppresses voltage caused at the terminal 127a of the primary winding of the transformer 103 by back electromotive force when the N channel MOSFET 126 is turned off. The diode 111 suppresses voltage caused at the terminal 127a of the primary winding of the transformer 103 by back electromotive force when the N channel MOSFET 126 is turned off so that the voltage at the terminal 127a is at an optimum level. The diode 111 also prevents current in the P channel MOSFET 110 from flowing in a reverse direction by voltage which will be caused by higher voltage than the source voltage at the terminal 127a of the transformer 103 when the N channel MOSFET 126 is turned on. The resistor 112 limits the gate current of the N channel MOSFET 114. The resistor 113 equalizes the gate potential of the N channel MOSFET 114 to the potential of the source. The N channel MOSFET 114 controls the supply of current to the primary winding of the transformer 103. The capacitor 115 smoothes source voltage supplied to the transformer 103. The capacitor 116 contributes to speedup when the bipolar transistor 120 is turned on or turned off. The resistor 117 limits the base current of the bipolar transistor 120. The resistor 118 equalizes the base potential of the bipolar transistor 120 to the potential of the collector. The resistor 119 limits the collector current of the bipolar transistor 120. The bipolar transistor 120 controls turning on/off the P channel MOSFET 122. The resistor 121 equalizes the gate potential of the P channel MOSFET 122 to the potential of the source. The P channel MOSFET 122 suppresses voltage caused at the terminal 127d of the primary winding of the transformer 103 by back electromotive force when the N channel MOSFET 114 is turned off. The diode 123 suppresses voltage caused at the terminal 127d of the primary winding of the transformer 103 by back electromotive force when the N channel MOSFET 114 is turned off so that the voltage is at an optimum level. The diode 123 also prevents current in a reverse direction from flowing in the P channel MOSFET 122 by voltage which will be caused by higher voltage than the source voltage at the terminal 127d of the transformer 103 when the N channel MOSFET 114 is turned on. The resistor 124 limits the base current of the N channel MOSFET 126. The resistor 125 equalizes the gate potential of the N channel MOSFET 126 to the potential of the source. The N channel MOSFET 126 controls the supply of current to the primary winding of the transformer 103. The transformer 103 insulates between the primary side and the secondary side of the semiconductor switch driving circuit, insulates each stage of the secondary side and transmits power from the primary side to the secondary side. The Zener diode 128a connects a positive voltage supply path to the switching device (IGBT) 133a and prevents voltage caused between the terminals 127e and 127f of the secondary winding of the transformer 103 by back electromotive force of the transformer 103. The Zener diode 129a connects a negative voltage supply path to the switching device (IGBT) 133a and prevents voltage caused between the terminals 127e and 127f of the secondary winding of the transformer 103 by back electromotive force of the transformer 103. The resistor 130a equalizes the gate potential of the switching device (IGBT) 133a to the potential of the emitter. The capacitor 131a keeps the gate voltage of the switching device (IGBT) 133a and corrects dispersion in the gate capacitance between the plural switching devices (IGBT) 133a and 133b. The resistor 132a limits the gate current of the switching device (IGBT) 133a. The switching device (IGBT) 133a causes or prevents the current for switching 134 to flow. Also, the driving section (including the Zener diodes 128b and 129b, the resistor 130b, the capacitor 131b and the resistor 132b) of the switching device (IGBT) 133b at the second stage similarly functions. Next, referring to the circuit diagram shown in Fig. 1 and timing charts shown in Figs. 2 (a) to (c), the operation of the semiconductor switch driving circuit equivalent to this embodiment will be described. Fig.2 (a) shows operation for keeping the semiconductor switch conducting (continuously supplying positive voltage). The operation in the primary side area 101 of the semiconductor switch driving circuit in this operation is as described in the following a-1 to a-8. a-1: Signals N and NL input to the primary side area 101 of the semiconductor switch driving circuit are kept 0 V on the circuit. a-2: The level of an input signal PL is changed from 0 V to a level at which the bipolar transistor 108 can be turned on (for example, +5 V). a-3: The bipolar transistor 108 becomes a conducting state. a-4: The P channel MOSFET 110 becomes a conducting state. a-5: After time enough to turn off the bipolar transistor 120 and the P channel MOSFET 122 elapses (for example, in 1 µs.) after the level of the input signal NL is made to 0 V in a-1, the level of an input signal P is changed from 0 V to a level at which the N channel MOSFET 126 can be turned on (for example, +5 V). a-6: The N channel MOSFET 126 becomes a conducting state. a-7: Current flows from the terminal 127c to the terminal 127d in the primary winding of the transformer 103 from the center tap 135 toward the N channel MOSFET 126. a-8: Electromotive force V2p which is positive on the side of the terminal 127e and is negative on the side of the terminal 127f (is similarly positive on the side of the terminal 127g and is similarly negative on the side of the terminal 127h) is generated at both ends of each secondary winding of the transformer 103 (refer to the following mathematical equation 1). V2p = V1 x N2/N1 In the mathematical equation 1, V1 denotes voltage applied between the terminals 127c and 127d of the transformer 103, N1 denotes the number of turns between the terminals 127c and 127d and between the terminals 127a and 127b of the transformer 103 and N2 denotes the number of turns between the terminals 127e and 127f and between the terminals 127g and 127h of the transformer 103. Next, the operation in the secondary side area 102 of the semiconductor switch driving circuit in this operation is as described in the following a-9 to a-18. The driving section of one switching device (IGBT) 133a of the semiconductor switch having plural stages will be described below, however, the operation of the switching device (IGBT) 133b at another stage and others are also similar. a-9: Electromotive force V2p at both ends of each secondary winding increases and exceeds voltage acquired by adding Zener voltage V z29 of the Zener diode 129a and the dropout voltage V f28 in a forward direction of the Zener diode 128a (refer to a mathematical equation 2). V2P > V z29 + V f28 a-10: The Zener diode 129a becomes a conducting state. a-11: The capacitor 131a is charged (the side of the Zener diode 129a is positive) and the gate capacitance of the switching device (IGBT) 133a is charged (the side of the gate is positive) via the resistor 132a. a-12: The gate voltage V GE of the switching device (IGBT) 133a exceeds the gate threshold voltage V GE(TH) (a condition of the mathematical equation 3) and the switching device (IGBT) 133a becomes a conducting state. V GE33 > V GE(TH) a-13: After the gate voltage V GE33 of the switching device (IGBT) 133a becomes at a level (for example, +15 V) enough to keep the switching device conducting (for example, in 2.5 µs.), an input signal P is made to 0 V. a-14 : The N channel MOSFET 126 becomes a non-conducting state. a-15: Back electromotive force which is positive on the side of the terminal 127d and is negative on the side of the terminal 127a is caused on the primary winding of the transformer 103, however, as the terminal 127a on one side of the winding is connected to a power source via the P channel MOSFET 110 and the diode 111 which are respectively in a conducting state, back electromotive force V1 rev caused between the terminals 127a and 127d is inhibited as shown in a mathematical equation 4. V1 rev = (V d*10 + V f11 ) x 2 V d*10 denotes the dropout voltage of the P channel MOSFET 110 and V f11 denotes the dropout voltage in a forward direction of the diode 111. a-16: Electromotive force V2p rev which is positive on the side of the terminal 127f and is negative on the side of the terminal 127e is also caused on the secondary winding by back electromotive force V1 rev caused on the primary winding of the transformer 103, however, the level is Zener voltage V z28 of the Zener diode 128a or less and the circuit on the secondary side becomes a non-conducting state by the Zener diode 128a (refer to a mathematical equation 5). V2p rev = (V1 rev x N2/N1) < V z28 a-17: The gate voltage V GE33 of the switching device (IGBT) 133a decreases according to a time constant determined based upon the resistor 130a, the capacitor 131a and the resistor 132a and the gate capacitance of the switching device (IGBT) 133a. This time constant is determined so that the gate voltage V GE33 of the switching device (IGBT) 133a can continue to keep the voltage enough to keep the switching device conducting for time enough for magnetic energy stored in the core of the transformer 103 to be consumed. a-18: Before the gate voltage V GE33 of the switching device (IGBT) 133a is the gate threshold voltage V GE<TH> or less and after magnetic energy stored in the core of the transformer 103 is consumed, the level of an input signal P is changed from 0 V to a level at which the N channel MOSFET 126 can be turned on (for example, +5 V). Afterward, a-6 to a-18 are repeated. The same operation is also performed at the same timing in the driving sections of the switching device (IGBT) 133b at another stage and others. Fig. 2 (b) shows operation for keeping the semiconductor switch non-conducting (continuously supplying negative voltage). The operation in the primary side area 101 of the semiconductor switch driving circuit in this operation is as described in the following b-1 to b-8. b-1: Signals P and PL input to the primary side area 101 of the semiconductor switch driving circuit are kept 0 V on the circuit. b-2: The level of an input signal NL is changed from 0 V to a level at which the bipolar transistor 120 can be turned on (for example, +5 V). b-3: The bipolar transistor 120 becomes a conducting state. b-4: The P channel MOSFET 122 becomes a conducting state. b-5: After time enough to turn off the bipolar transistor 108 and the P channel MOSFET 110 elapses (for example, in 1 µs.) after the input signal PL is made to 0 V, the level of an input signal N is changed from 0 V to a level at which the N channel MOSFET 114 can be turned on (for example, +5 V). b-6: The N channel MOSFET 114 becomes a conducting state. b-7: Current flows (from the terminal 127b to the terminal 127a) in the primary winding of the transformer 103 from the center tap toward the N channel MOSFET 114. b-8: Electromotive force V2n which is positive on the side of the terminal 127f and is negative on the side of the terminal 127e (is similarly positive on the side of the terminal 127h and is similarly negative on the side of the terminal 127g) is generated at both ends of each secondary winding of the transformer 103 (refer to a mathematical equation 6). V2n = V1 x N2/N1 V1 denotes voltage applied between the terminals 127b and 127a of the transformer 103, N1 denotes the number of turns between the terminals 127a and 127b and between the terminals 127c and 127d of the transformer 103 and N2 denotes the number of turns between the terminals 127e and 127f and between the terminals 127g and 127h of the transformer 103. Next, the operation in the secondary side area 102 of the semiconductor switch driving circuit in this operation is as described in the following b-9 to b-18. The driving section of one switching device (IGBT) 133a of the semiconductor switch at plural stages will be described, however, the operation of the switching device (IGBT) 133b at another stage and others is also similar. b-9: Electromotive force V2n at both ends of each secondary winding increases and exceeds voltage acquired by adding Zener voltage V z28 of the Zener diode 128a and the dropout voltage V f29 in a forward direction of the Zener diode 129a. V2n > V z28 + V f29 b-10: The Zener diode 128a becomes a conducting state. b-11: The capacitor 131a is charged (the side of the Zener diode 129a is negative) and the gate capacitance of the switching device (IGBT) 133a is charged (the side of the gate is negative) via the resistor 132a. b-12: The gate voltage V GE of the switching device 133a becomes negative and the switching device is forcedly non-conducting. b-13: After the gate voltage V GE of the switching device 133a becomes at a level (for example, -15 V) enough to keep the switching device non-conducting (for example, in 2.5 µs.), an input signal N is made to 0 V. b-14: The N channel MOSFET 114 becomes a non-conducting state. b-15: Back electromotive force which is positive on the side of the terminal 127a and is negative on the side of the terminal 127d is caused on the primary winding of the transformer 103, however, as the terminal 127d at one end of the winding is connected to a power source via the P channel MOSFET 122 and the diode 123 which are respectively in a conducting state, the caused back electromotive force V1 rev is inhibited as shown in the following mathematical equation 8. V1 rev = (V ds22 + V f23 ) x 2 V ds22 denotes the dropout voltage of the P channel MOSFET 122 and V f23 denotes the dropout voltage in a forward direction of the diode 123. b-16: Electromotive force V2n rov which is positive on the side of the terminal 127e and is negative on the side of the terminal 127f is also generated on the secondary winding by back electromotive force V1 rev caused on the primary winding of the transformer 103, however, the level is Zener voltage V z29 of the Zener diode 129a or less and the circuit on the secondary side becomes a non-conducting state by the Zener diode 129a (refer to a mathematical equation 9). V2n rev = (V1 rev x N2/N1) < V z29 b-17: The gate voltage V GE33 of the switching device (IGBT) 133a increases according to a time constant determined based upon the resistor 130a, the capacitor 131a and the resistor 132a and the gate capacitance of the switching device (IGBT) 133a. This time constant is determined so that the gate voltage V GE33 of the switching device (IGBT) 133a can continue to keep the voltage enough to keep the switching device non-conductive for time enough for magnetic energy stored in the core of the transformer 103 to be consumed. b-18: Before the gate voltage V GE33 of the switching device (IGBT) 133 is the threshold 0 V or more and after magnetic energy stored in the core of the transformer 103 is consumed, the level of an input signal N is changed from 0 V to a level at which the N channel MOSFET 114 can be turned on (for example, +5 V). Afterward, b-6 to b-18 are repeated. The same operation is also performed at the same timing in the driving sections of the switching device (IGBT) 133b at another stage and others. Fig. 2(c) shows The switching operation of the semiconductor switch (The switching operation of IGBT by switching positive voltage and negative voltage). The operation in the primary side area 101 of the semiconductor switch driving circuit in this operation is as described in the following c-1 to c-8. c-1: Signals N and NL input to the primary side area 101 of the semiconductor switch driving circuit are made to 0 V on the circuit. c-2: The level of an input signal PL is changed from 0 V to a level at which the bipolar transistor 108 can be turned on (for example, +5 V). c-3: The bipolar transistor 108 becomes a conducting state. c-4: The P channel MOSFET 110 becomes a conducting state. c-5: After time enough to turn off the bipolar transistor 120 and the P channel MOSFET 122 elapses (for example, in 1 µs.) after the input signal NL is made to 0 V, the level of an input signal P is changed from 0 V to a level at which the N channel MOSFET 126 can be turned on (for example, +5 V). c-6: The N channel MOSFET 126 becomes a conducting state. c-7: Current flows (from the terminal 127c to the terminal 127d) in the primary winding of the transformer 103 from the center tap toward the N channel MOSFET 126. c-8: Electromotive force V2p which is positive on the side of the terminal 127e and is negative on the side of the terminal 127f (is similarly positive on the side of the terminal 127g and is similarly negative on the side of the terminal 127h) is generated at both ends of each secondary winding of the transformer 103. V2p = V1 x N2/N1 V1 denotes voltage applied between the terminals 127c and 127d of the transformer 103, N1 denotes the number of turns between the terminals 127c and 127d and between the terminals 127a and 127b of the transformer 103 and N2 denotes the number of turns between the terminals 127e and 127f and between the terminals 127g and 127h of the transformer 103. Next, the operation in the secondary side area 102 of the semiconductor switch driving circuit in this operation is as described in the following c-9 to c-34. The driving section of one switching device (IGBT) 133a of the semiconductor switch at plural stages will be described, however, the operation of the switching device (IGBT) 133b at another stage and others is also similar. c-9: Electromotive force V2p at both ends of each secondary winding increases and exceeds voltage acquired by adding Zener voltage V z29 of the Zener diode 129a and the dropout voltage V f28 in a forward direction of the Zener diode 128a. V2p > V z29 + V f28 c-10: The Zener diode 129a becomes a conducting state. c-11: The capacitor 131a is charged (the side of the Zener diode 129a is positive) and the gate capacitance of the switching device (IGBT) 133a is charged (the side of the gate is positive) via the resistor 132a. c-12: The gate voltage V GE33 of the switching device (IGBT) 133 exceeds the gate threshold voltage V GE(TH) (refer to a mathematical equation 12) and the switching device (IGBT) 133a becomes a conducting state. V GE33 > V GE<TH> c-13: After the gate voltage V GE33 of the switching device (IGBT) 133a becomes at a level (for example, +15 V) enough to keep the switching device conducting (for example, in 2.5 µs.), an input signal P is made to 0 V. c-14 : The N channel MOSFET 126 becomes a non-conducting state. c-15: Back electromotive force which is positive on the side of the terminal 127d and is negative on the side of the terminal 127a is caused on the primary winding of the transformer 103, however, as the terminal 127a at one end of the winding is connected to a power source via the P channel MOSFET 110 and the diode 111 which are respectively in a conducting state, back electromotive force V1 rev caused between the terminals 127a and 127d is inhibited as shown in the following mathematical equation 13. V1 rev = (V ds10 + V f11 ) x 2 V ds10 denotes the dropout voltage of the P channel MOSFET 110 and V f11 denotes the dropout voltage in a forward direction of the diode 111. c-16: Electromotive force V2p rev which is positive on the side of the terminal 127f and is negative on the side of the terminal 127e is also generated on the secondary winding by back electromotive force V1 rev caused on the primary winding of the transformer 103, however, the level is Zener voltage V z28 of the Zener diode 128a or less and the circuit on the secondary side becomes a non-conducting state by the Zener diode 128a. V2p rev = (V1 rev x N2/N1) < V z28 c-17: The gate voltage V GE33 of the switching device (IGBT) 133a decreases according to a time constant determined based upon the resistor 130a, the capacitor 131a and the resistor 132a and the gate capacitance of the switching device (IGBT) 133a. This time constant is determined so that the gate voltage V GE33 of the switching device (IGBT) 133a can continue keeping the voltage enough to keep the switching device conducting for time enough for magnetic energy stored in the core of the transformer 103 to be consumed. c-18: Before the gate voltage V GE33 of the switching device (IGBT) 133 is the gate threshold voltage V GE<TH> or less and after magnetic energy stored in the core of the transformer 103 is consumed, the level of the input signal PL is made to 0 V. Simultaneously, the level of the input signal NL is changed from 0 V to a level at which the bipolar transistor 120 can be turned on (for example, +5 V). c-19: The bipolar transistor 120 becomes a conducting state. c-20: The P channel MOSFET 122 becomes a conducting state. c-21: After time enough to turn off the bipolar transistor 108 and the P channel MOSFET 110 elapses (for example, in 1 µs.) after the input signal PL is made to 0 V, the level of an input signal N is changed from 0 V to a level at which the N channel MOSFET 114 can be turned on (for example, +5 V). c-22: The N channel MOSFET 114 becomes a conducting state. c-23: Current flows (from the terminal 127b to the terminal 127a) in the primary winding of the transformer 103 from the center tap toward the N channel MOSFET 114. c-24: Electromotive force V2n which is positive on the side of the terminal 127f and is negative on the side of the terminal 127e (is similarly positive on the side of the terminal 127h and is similarly negative on the side of the terminal 127g) is generated at both ends of each secondary winding of the transformer 103 (refer to a mathematical equation 15). V2n = V1 x N2/N1 V1 denotes voltage applied between the terminals 127b and 127a of the transformer 103, N1 denotes the number of turns between the terminals 127a and 127b (and between the terminals 127c and 127d) of the transformer 103 and N2 denotes the number of turns between the terminals 127e and 127f (and between the terminals 127g and 127h) of the transformer 103. c-25: Electromotive force V2n at both ends of each secondary winding increases and exceeds voltage acquired by adding Zener voltage V z28 of the Zener diode 128a and the dropout voltage V f29 in a forward direction of the Zener diode 129a. V2n > V z28 + V f29 c-26: The Zener diode 128a becomes a conducting state. c-27: The capacitor 131a is charged (the side of the Zener diode 129a is negative) and the gate capacitance of the switching device (IGBT) 133a is charged (the side of the gate is negative) via the resistor 132a. c-28: The gate voltage V GE of the switching device (IGBT) 133a becomes negative and the switching device is forcedly non-conducting. c-29: After the gate voltage V GE of the switching device (IGBT) 133a becomes at a level (for example, -15 V) enough to keep the switching device non-conducting (for example, in 2.5 µs.), the input signal N is made to 0 V. c-30: The N channel MOSFET 114 becomes a non-concluding state. c-31: Back electromotive force which is positive on the side of the terminal 127a and is negative on the side of the terminal 127d is caused on the primary winding of the transformer 103, however, as the terminal 127d at one end of the winding is connected to a power source via the P channel MOSFET 122 and the diode 123 which are respectively in a conducting state, the caused back electromotive force V1 rev is inhibited as shown in a mathematical equation 17. V1 rev = (V ds22 + V f23 ) x 2 V ds22 denotes the dropout voltage of the P channel MOSFET 122 and V f23 denotes the dropout voltage in a forward direction of the diode 123. c-32: Electromotive force V2n rev which is positive on the side of the terminal 127e and is negative on the side of the terminal 127f is also generated on the secondary winding by back electromotive force V1 rev caused on the primary winding of the transformer 103, however, the level is Zener voltage V z29 of the Zener diode 129a or less and the secondary side becomes a non-concluding state by the Zener diode 129a. V2n rev = (V1 rev x N2/N1) < V z29 c-33: The gate voltage V GE33 of the switching device (IGBT) 133a increases according to a time constant determined based upon the resistor 130a, the capacitor 131a and the resistor 132a and the gate capacitance of the switching device (IGBT) 133a. This time constant is determined so that the gate voltage V GE33 of the switching device (IGBT) 133a can keep the voltage enough to keep the switching device non-conducting for time enough for magnetic energy stored in the core of the transformer 103 to be consumed. c-34: Before the gate voltage V GE33 of the switching device (IGBT) 133a is the threshold 0 V or more and after magnetic energy stored in the core of the transformer 103 is consumed, the level of the input signal NL is made to 0 V. Simultaneously, the level of the input signal PL is changed from 0 V to a level at which the bipolar transistor 108 can be turned on (for example, +5 V). Afterward, c-3 to c-34 are repeated. The same operation is also performed at the same timing in the driving sections of the switching device (IGBT) 133b at another stage and others. As the semiconductor switch driving circuit equivalent to this embodiment can be used for a semiconductor switch of a circuit for generating a high-voltage electric pulse, a high-voltage electric pulse can be stably supplied from the output terminal of electrotherapy apparatus provided with the semiconductor switch to an outside living body. Also, the semiconductor switch circuit equivalent to this embodiment can perform high-speed switching operation about 35 Hz. As described above in detail, in the semiconductor switch driving circuit according to the first aspect, as voltage between the gate and the emitter of the switching device can be continuously kept positive, voltage between the gate and the emitter can be continuously kept negative, voltage between the gate and the emitter can be alternately switched to positive voltage or negative voltage, the stable conducting state of the semiconductor switch can be kept, the stable non-conducting state of the semiconductor switch can be kept. As the semiconductor switch driving circuit according to the second and third aspect causes or prevents current to flow for switching when a control signal is input, the semiconductor switch which can be operated in synchronization with an input control signal can be realized. As the semiconductor switch driving circuit according to the fourth aspect is configured so that the source of the P channel MOSFET is connected to the power terminal, the drain of the P channel MOSFET is connected to the anode of the diode, the cathode of the diode is connected to the terminal at one end of the primary winding of the transformer and back electromotive force between the terminal at one end of the primary winding of the transformer and the terminal at the other end of the primary winding of the transformer can be inhibited by placing the P channel MOSFET into a conducting state, the stable operation of the semiconductor switch can be realized by inhibiting the back electromotive force. The semiconductor switch driving circuit according to the fifth aspect can transmit power for controlling plural switching devices to the secondary side area by the circuit configuration in the primary side area, can absorb back electromotive force caused when current flowing in the transformer is cut off and the stable operation of the semiconductor switch can be realized by the simple circuit and the small number of parts. As the semiconductor switch driving circuit according to the sixth aspect is provided with plural switching devices and plural gate driving sections that directly drive the switching devices in the secondary side area and the switching devices are connected in series, the withstand voltage of the semiconductor switch against the application of high voltage has a value acquired by adding the withstand voltage of the switching device itself at each stage and the high-withstand voltage semiconductor switch can be realized. As the switching device in the semiconductor switch driving circuit according to the seventh aspect is an insulated gate bipolar transistor (IGBT), the semiconductor switch which can use the device (IGBT) provided with both the low saturation voltage characteristic of the bipolar transistor and the switching characteristic of power MOSFET can be realized. As the semiconductor switch driving circuit according to the eighth aspect is provided with the Zener diode for preventing electromotive force caused on the secondary winding by back electromotive force caused on the primary winding of the transformer in the secondary side area, the stable operation of the semiconductor switch can be realized. As in the secondary side of the semiconductor switch driving circuit according to the ninth aspect, the terminal at one end of the secondary winding of the transformer is connected to the anode of the first Zener diode, the anode of the second Zener diode the cathode of which is directly connected to the cathode of the first Zener diode in series with both cathodes face to face is connected to the gate of the specific switching device via the first resistor, the terminal at the other end of the secondary winding of the transformer is connected to the emitter of the specific switching device, the second resistor and the capacitor are connected between the anode of the second Zener diode and the emitter of the specific switching device and the plural specific switching devices are provided, the stable semiconductor switch which receives power supplied from the primary side area, can transmit the power for controlling the plural switching devices to the plural switching devices and can reduce a lag of switching timing between the switching devices can be realized by the simple circuit and the small number of parts. As the electrotherapy apparatus according to the tenth aspect can keep the stable conducting state of the semiconductor switch, can keep the stable non-conducting state of the semiconductor switch, enables the switching operation of the semiconductor switch, can minimize a lag of the switching timing of each switching device and can realize the semiconductor switch by the simple circuit and the small number of parts respectively by using the semiconductor switch driving circuit according to any of the first to the ninth aspects for the semiconductor switch of the circuit for generating a high-voltage electric pulse, the electrotherapy apparatus ensuring high operational stability can be provided at lower cost.

Claims: A semiconductor switch driving circuit (100) comprising: a transformer (103); a primary side area (101) provided on the primary side of the transformer (103) for controlling current on the primary side of the transformer according to a control signal for controlling a semiconductor switch; and a secondary side area (102) provided on the secondary side of the transformer for directly driving a switching device (133a, 133b) wherein said secondary side area is arranged so that the secondary side is capable of maintaining the voltage between the gate and the emitter of the switching device (133a, 133b) as one selected from a state of being continuously kept positive, being continuously kept negative and being alternately switched between positive and negative A semiconductor switch driving circuit according to claim 1, wherein, in the primary side area (101), the control signal is input to transmit power to the secondary side area for controlling plural switching devices (133a, 133b) of the secondary side area (102) and back electromotive force caused when current flowing in the transformer (103) is cut off is absorbed. A semiconductor switch driving circuit according to claim 1, wherein the secondary side area (102) receives the power supplied from the primary side area (101) and transmits the power for controlling plural switching devices to switching devices (133a, 133b), and the plural switching devices receive the power supplied to the secondary side area (102) and cause or prevent current to flow for switching. A semiconductor switch driving circuit according to claim 1, wherein the source of P channel MOSFET (110) is connected to a power terminal (VDD), the drain of the P channel MOSFET (110) is connected to the anode of a diode (111), the cathode of the diode is connected to a terminal (127a) at one end of a primary winding of the transformer (103) and back electromotive force between the terminal (127a) at one end of the primary winding of the transformer (103) and a terminal (127b) at the other end of the primary winding is inhibited when the P channel MOSFET (110) conducts. A semiconductor switch driving circuit according to claim 4, wherein in the primary side area (101), a control signal input terminal (PL) is connected to the base of an NPN bipolar transistor (108) via a resistor (105) and a capacitor (104) respectively connected in parallel, the base and the emitter of the NPN bipolar transistor (108) are connected via a resistor (106) and the emitter is connected to a ground terminal (GND),the collector of the NPN bipolar transistor (108) is connected to the gate of the P channel MOSFET (110) via a resistor (107), the gate and the source of the P channel MOSFET (110) are connected via a resistor (109) to the power terminal (VDD), the cathode of the diode (111) is connected to the drain of a N channel MOSFET (114), the gate and the source of the N channel MOSFET (114) are connected via a resistor (113) and the source is connected to a ground terminal (GND), a control signal input terminal (N) is connected to the gate of the N channel MOSFET (114) via a resistor (112), a control signal input terminal (NL) is connected to the base of an NPN bipolar transistor (120) via a resistor (117) and a capacitor (116) respectively connected in parallel, the base and the emitter of the NPN bipolar transistor (120) are connected via a resistor (118) and the emitter is connected to a ground terminal (GND), the collector of the NPN bipolar transistor (120) is connected to the gate of a P channel MOSFET (122) via a resistor (119), the gate and the source of the P channel MOSFET (122) are connected via a resistor (121) and the source is connected to the power terminal (VDD), the drain of the P channel MOSFET (122) is connected to the anode of a diode (123),the cathode of the diode (123) is connected to the drain of a N channel MOSFET (126) and a terminal (127d) of the primary winding of the transformer (103), the gate and the source of the N channel MOSFET (126) are connected via a resistor (125) and the source is connected to the ground terminal (GND), a control signal input terminal (P) is connected to the gate of the N channel MOSFET (126) via a resistor (124), the terminals (127b, 127c) of the primary winding of the transformer (103) are connected to a center tap (135), the center tap (135) is connected to the power terminal (VDD) and is connected to the ground terminal (GND) via a capacitor (115). A semiconductor switch driving circuit according to claim 2, wherein the secondary side area (102) is provided with said plural switching devices (133a, 133b) and plural gate driving sections (136a, 136b) for respectively directly driving the switching devices (133a, 133b) which are connected in series. A semiconductor switch driving circuit according to claim 6, wherein the switching device (133a, 133b) is an insulated gate bipolar transistor (IGBT). A semiconductor switch driving circuit according to any one of claim 1 or 7, wherein the secondary side area (102) has a Zener diode (128a, 129a, 128b, 129b) for preventing electromotive force generated on a secondary winding by back electromotive force caused on a primary winding of the transformer (103). A semiconductor switch driving circuit according to claim 8, wherein, in the secondary side area (102), a terminal (127e) at one end of a secondary winding of the transformer (103) is connected to a first Zener diode (128a), a second Zener diode (129a) is connected to a gate of a specific switching device (133a) via a first resistor (132a), wherein same kind of polarities of the first and the second Zener diode (128a, 129a) are directly connected in series with the polarities face to face, a terminal (127f) at the other end of the secondary winding of the transformer (103) is connected to the emitter of the specific switching device (133a), a second resistor (130a) and a capacitor (131a) are connected between the second Zener diode (129a) and the emitter of the specific switching device (133a), and wherein a structure comprising the secondary winding of the transformer (103) and the switching device (133a) connected via a gate driving section (136a) is plurally provided. An semiconductor switch driving circuit according to any of claim 1 to 9 is used in a electrotherapy apparatus for generating a high voltage electric pulse.

Inventors: AKIYAMA NAOTO, INOMATA MASAHIKO, TSUMURA IKUHIRO, AKIYAMA, NAOTO, INOMATA, MASAHIKO, TSUMURA, IKUHIRO
Applicants: NIHON KOHDEN CORP, NIHON KOHDEN CORPORATION
Application year: 2001
Main classification: H03K17
IPC codes: H03K17, H02M1