FRACTAL AND SPACE-FILLING TRANSMISSION LINES, RESONATORS, FILTERS AND PASSIVE NETWORK ELEMENTS

Abstract: This invention relates to high frequency electromagnetic circuits, in particular to those made on planar or quasi-planar substrates, where the circuit is patterned on a metallic or superconducting film on top of a dielectric in any of the configurations known to those skilled in the art (for instance micro-strip, strip-line, co-planar, parallel plate or slot-line configurations). A part of the circuit such as the characteristic strip or slot of said configurations is shaped in a novel space-filling or fractal geometry which allows a significant size reduction of the circuital component. Miniature transmission lines, capacitors, inductors, resistors, filters and oscillators can be manufactured this way.

Description: FRACTAL AND SPACE-FILLING TRANSMISSION LINES, RESONATORS, FILTERS AND PASSIVE NETWORK ELEMENTS DESCRIPTION Object of the Invention This invention relates to high frequency electromagnetic circuits, in particular to those made on planar or quasi-planar substrates, where the circuit is patterned on a metallic or superconducting film on top of a dielectric in any of the configurations known to those skilled in the art (for instance micro-strip, strip-line, co-planar, parallel plate or slot-line configurations) . A part of the circuit such as the characteristic strip or slot of said configurations is shaped in a novel spacefilling geometry which allows a significant size reduction of the circuital component. Miniature transmission lines, capacitors, inductors, resistors, filters and oscillators can be manufactured this way. The invention is preferably applicable to the telecommunications field and more concretely to high frecuency electromagnetic circuits. Background and Summary of the Invention There are many applications where planar circuits are used which would benefit from a reduction in the circuit size. This is the case, for example, in aerospace applications and mobile communication systems where weight and volume of the equipment is severely restricted. This reduction is also desirable when the cost of a substrate (the dielectric and metals or superconductors covering it) is high. The present invention relates to miniaturization techniques of planar electromagnetic circuits, with an emphasis on circuits containing resonators such as filters and oscillators. As described below, these techniques can also be used to reduce the size of individual components within a planar circuit, even though the overall function of the circuit might not be that of a filter. A novel type of geometries is proposed to pattern said circuits and components, so that an efficient use of substrate space is made . Figure 18 shows the layout of a standard, two-port microstrip resonator (prior art) used in planar microwave and RF circuits. This is also the simplest form of a microwave planar filter, since signal transfer between the input and output port occurs only at frequencies close to the half-wave resonance of the open-circuited microstrip line. More elaborate filter designs consist in coupling several resonant lines, and there are many design alternatives as described in GL Matthaei, L Young, EMT Jones, Microwave Filters, Impedance-Matching Networks and Coupling Structures. Artech House, Dedham, MA 1980. For example, Figure 20 represents a multipole planar filter made by coupling several resonant lines through their ends (prior art). Although more space-efficient filter layouts exist, this figure clearly shows that there is a tradeoff between the number of resonators in a filter and the surface that it takes in the planar substrate. Furthermore, since the number of resonators in a filter determines its frequency selectivity and the ripple in its passband, this number is not a parameter that is likely to be changed for the sake of a reduced filter size. The present invention provides some geometries to efficiently fold and coil the resonators in filters with coupled-line resonators (as the ones in Figs 18 and 20, among many other filter topologies), so that an efficient use of the substrate space is made. This allows for a high number of resonators to be used in a planar filter. Some preliminary attempts to fold the resonant lines within a filter have been reported in a various published works, a clear example being the Hairpin filters described in E.G. Crystal, S. Frankel "Hairpin-Line and Hybrid Hairpin-Line / Half-Wave Parallel-Coupled-Line Filters", IEEE Trans on Microw. Theor. and Tech. Vol. 20, No. 11, November 1972 pp. 719-728 (Figure 31) . These are essentially typical half-wave parallel-coupled-line filters in which the line resonators are folded in half. However, the folding schemes used there are not the most efficient way of reducing the size of the device. Instead, in this invention patent alternative shaping procedures using multiple line segments arranged in novel space-filling geometries are introduced. As an example of the need in improving the miniaturization techniques described in the prior art, some modifications to the original design of the Hairpin filter have been already described in the technical literature. For example, G.L. Matthaei, N.O. Frenzi, R.J. Forse and S.M. Rohlfing in "Hairpin-Comb Filters for HTS and Other Narrow-Band Applications", IEEE Trans on Microw. Theor. and Tech. Vol. 45, No. 8, August 1997 pp. 1226- 1231, use the modified Hairpin resonator of Figure 32.1 in which the size of the resonator is modified by introducing capacitive coupling between its ends by means of a straight slot. Following the spirit of the present invention, it is proposed here a further reduction of the size of said resonator by replacing the straight coupling slot with the more convoluted geometries disclosed in this document. An even further reduction would be obtained by also replacing the U-shaped strip by said geometries of the present invention. Another known technique for reducing the filter size is to use slow-wave transmission lines or other related slow-wave guiding structures instead of the standard lines in the resonators of the filter. This reduces the length of the line resonators used in the filter. A prior art example of slow-wave line is the ladder line described by J.S. Hong and M.J. Lancaster in "Superconducting Filters Using Slow Wave Transmission Lines", Microwave and Optical Technology Letters, Vol. 9, No. 4, July 1995, pp207-210 (Figure 22), in which the solid strip conductor of a typical microstrip line is replaced by a ladder-like structure. This significantly reduces the propagation velocity in the ladder line with respect to that of a standard microstrip line. The reduction in velocity is due to the high inductance of the two long, parallel strips (the handle bars in the ladder), and the high capacitance provided by the multiple parallel strips connecting them (the steps in the ladder) . The geometrical shapes covered in the present invention can also be used to produce slow-wave transmission lines and guiding structures, and to further reduce the velocity of propagation (and thus, size) of prior art topologies of slow-wave lines. For example, the straight-line step-like strips in Figure 22 can be substituted for the more convoluted geometries of this invention to further reduce the velocity of propagation. Another known filter miniaturization technique is the use of dual and degenerate resonant modes as described, among many other references, by S.L. Fiedziuszko, J. A. Curtis in patent US5172084. Said patent is based on resonant structures made of microstrip ring resonators. More compact resonators, also supporting dual modes, can be built using the geometries proposed in the present invention. Not all planar filters are made by coupling structures that show an electromagnetic resonance within the passband of the filter. For example, D Zhang, G-C Liang, CF Shih, RS Withers in "Narrowband Lumped-Element Microstrip Filters Using Capacitively - Loaded Inductors" (1995 MTT-S Symposium Digest. Orlando, Florida, May 1995. pages 379-382 vol.2) present a filter whose passband frequencies are well below the resonant frequencies of the resonators used. These filters need reactances to implement the resonators and to provide coupling among said resonators. These reactances can also be made smaller by using the geometries of the present invention. For example, in said paper by Zhang et al, interdigitated capacitances are used in the resonators. Said capacitances consist in a meander-shaped slot separating two strips. A reduction in the size of these resonators would be obtained if said meander would be replaced by the more convoluted geometries disclosed in the present invention. This is only a very specific example where said geometries can be applied to the miniaturization of reactive components in planar circuits. The invention is applicable wherever planar reactances are needed. This includes all type of filters (beyond the various type of filters described above), and any other circuit using DC blocks, RF chokes, capacitances, inductances or resonators. Some particular cases of the geometries used in the present invention were mathematically described in the end XIX century. Several mathematicians such as Georg Cantor, Giusepe Peano, David Hilbert, Helge von Koch and Waclaw Sierpinski described the construction of several curves and structures that inspire some of the designs showed in the present document. More recently, Benoit Mandelbrot (B.B. Mandelbrot, The Fractal Geometry of Nature, W.H. Freeman and Co., New York, 1982) coined the term fractal and introduced many other particular cases of similar geometries. In all said cases the curves were studied from the mathematical point of view but were never used for any practical engineering application. The most common way of designing some fractals shapes is by means of an Iterated Function System (IFS) geometric algorithm (sometimes also known as Multy Reduction Copy Machine, MRCM) . In some other cases networks of IFS or MRCM algorithms are used as well (the resulting algorithms are named NMRCM in those cases) . Said algorithms are based on Hutchinson operators. A Hutchinson operator is a set of linear transformations which, in case of a flat structure, said linear transformations are mathematically described as x„ [Vcosφ - s sinψ Yx„-i y (xΛ + n ) sinφ scosψ γ„. u y 0 j where (x n -i/ y n -ι) are the coordinates of the points of an input set An-i, {x nr Yn) are the points of an output set A n , (xo yo) define a translation transformation, r and s are real numbers corresponding to scaling factors and where φ and ψ define rotation transformations. Each linear transformation of a Hutchinson operator is characterized by the parameters r, s, φ and ψ plus the translation to (xo Yo) • A Hutchinson operator is characterized by its set of linear transformations. An IFS algorithm is an iterative procedure that consists in a first stage on applying a characteristic Hutchinson operator to an input set of points A0 to obtain an output set of points Al, and to keep applying the same Hutchinson operator to the output a number N of times (stages of the procedure) until a set of points AN is obtained. Strictly speaking, to generate a fractal shape the IFS algorithm has to be applied an infinite number of times (N((); also, the designer has to properly choose the linear transformations that compose the Hutchinson operator that characterizes the IFS algorithm. In a more complex procedure, several Hutchinson operators are applied at each stage and also several initial sets of points are used (for instance to generate the Hilbert and SZ curves described in Figure 1 and Figure 3 respectively) ; in this case, the term NMRCM is used to described the procedure. Both IFS (MRCM) and NMRCM procedures are well known to those skilled in the field of fractal mathematics; a more detailed discussion of their application to generate fractal structures is found in H.O.Peitgen, H.Jurgens, D.Saupe, Chaos and Fractals, Springer-Verlag, 1992. Of course a precise fractal structure or curve is a mathematical abstraction and cannot be physically implemented since requires an infinite number of iterations. In the present invention, some of the characteristic curves and structures used to shape some parts of the claimed electromagnetic devices are generated using said IFS and NMRCM algorithms with a finite number of stages N. The dimension (D) is often used to characterize highly convoluted geometrical curves and structures such as those described in the present invention. There exists many different mathematical definitions of dimension (see for instance a discussion of this topic in H.O.Peitgen, H.Jϋrgens, D.Saupe, Chaos and Fractals, Springer- Verlag,1992 ), but in the present document the box- counting dimension (which is well-known to those skilled in mathematics theory) is used to characterize a family of designs. A first attempt to use fractal geometry to construct a resonator is described in WO97/06578. The use of a fractal-shaped helical or spiral coil as an inductor together with a conventional capacitor to form a resonator was described there. As it can be readily seen by those skilled in the art, the present invention is essentially different from the particular case described in said patent application for several reasons: (a) the present invention includes the description of many network elements (capacitors, transmission lines, filters, resonators, inductors, resistors) that are not disclosed in said patent application. (b) The present invention describes the construction of distributed resonators and filters comprising distributed transmission lines and other distributed structures that do not require the use of a lumped inductor and a lumped capacitor to form the resonator. (c) Fractal and space-filling curve based planar capacitors are described in the present patent which are previously non-disclosed inventions. (d) In the cases of the present invention where resonators are formed with lumped inductors and capacitors, the inductors are constructed in a planar form by means non-intersecting curves and using geometries (space-filling curves and Hilbert, Peano and SZ curves as it is clearly detailed in the following sections) which are substantially distinct to those described in WO97/06578. (e) In those cases where the term fractal is used in the present invention, it is done in a different way as in WO97/06578; in particular a different definition of fractal dimension is used here (the Haussdorf and the box-counting dimension) as well as a different construction of the fractal curves. The curves used in the present invention (such as the Hilbert and SZ curves) require different construction mechanisms such as NMRCM algorithms that are not included in said patent application. The designs here should not be confused with other previously disclosed works such as M.Ishida, R.Mill "The electrical impedance of a continuously scaled fractal transmission line", J.Phys. D:Appl . Phs.30 (1997) (pages 1157-1163) . Such a theoretical scientific work analyses the theoretical behavior of a conceptual transmission line that features a fractal characteristic impedance (not a fractal-like geometry of the transmission line as it is introduced here) ; said work is an abstraction and does not describe the physical construction of any transmission line, and of course, it does not describe any use of said imaginary device either. A co-planar slow-line loaded by means of a convoluted planar capacitor is already described in M.J.Lancaster, F.Huang, A. Porch, J.S.Hong and D.Hung, "Superconducting Filters Using Slow-Wave Transmission Lines" Advances in Superconductivity. New Materials, Critical Current and Devices. Proceedings of the International Symposium. New Age Int, New Delhi, India; 1996 pp. 180-185, which in fact can be seen as a particular case of one of the slow-line co-planar structures described in the present invention patent document. Nevertheless, those skilled in the art will notice that the designs in the present invention patent are based on different curves and geometries (such as the Hilbert and SZ curve) not previously disclosed that can be used to further reduce the size of the slow-line. Summary of the Invention The key point of the invention is shaping part of the planar circuit (transmission lines, capacitors, resistors, inductors, resonators and filters) as a Space-Filling Curve (hereafter SFC) , that is, a curve that is large in terms of physical length but small in terms of the area in which the curve can be included. More precisely, the following definition is taken in the present document for a space-filling curve: a curve composed by at least ten segments which are connected in such a way that each segment forms an angle with their neighbours, that is, no pair of adjacent segments define a larger straight segment. Said space-filling curve can be fitted over a flat or curved surface, and due to the angles between segments, the physical length of the curve is always larger than that of any straight line that can be fitted in the same area (surface) as said space-filling curve. Also, whatever the design of such SFC is, it can never intersect with itself at any point except the initial and final point (that is, the whole curve can be arranged as a closed curve or loop, but none of the parts of the curve can become a closed loop) . When applying said SFC geometry to shape said planar circuit, it must be taken into account that said segments must be smaller than a tenth of the operating free-space wavelength. Depending on the shaping procedure and curve geometry, such space-filling curves can be designed to feature a Haussdorf dimension (for a precise definition of Haussdorf dimension see for instance H.O.Peitgen, H.Jurgens, D.Saupe, Chaos and Fractals, Springer-Verlag, New York, 1992) larger than their topological-dimension. That is, in terms of the classical Euclidean geometry, it is usually understood that a curve is always a one- dimension object; however when the curve is highly convoluted and its physical length is very large, the curve tends to fill parts of the surface which supports it; in that case the Haussdorf dimension can be computed over the curve (or at least an approximation of it by means of the box-counting algorithm) resulting in a number larger than unity. The curves in Figure 1 and Figure 3 are some examples of such SFC, featuring a dimension D « 2. Some particular cases of said SFC curves are often referred as "fractal" curves (see for instance B.B.Mandelbrot, The Fractal Geometry of Nature, W.H. Freeman and Company, 1983) . The term fractal describes a whole family of geometries (including sets of dots, curves, surfaces, ...) which usually feature the self- similarity property, that is, each part of the geometrical object is a replica of the whole object at a different scale. Strictly speaking a fractal curve is an ideal mathematical abstraction that has an infinite length, therefore in practice a true fractal curve cannot be physically constructed. At most, some fractal shapes can be approached with other non-fractal objects, for instance by means of the space-filling curves described above, or by means of a multilevel structure (PCT/ES99/00296) . For the sake of clarity, the term Fractal Space-Filling Curve (FSFC) is used in this document to name any of the SFC that substantially approach ' an ideal fractal shape. The advantage of using SFC, fractal or FSFC curves in the physical shaping of the circuital components is twofold: (a) Given a particular operating frequency or wavelength and a characteristic feature of the circuital component (the inductance of the inductor, the capacitance of the capacitor, the resistance of the resistor, the electrical length of the transmission line and so on) , said circuital component can be reduced in size with respect to prior art. (b) Given the physical size and the characteristic feature of the component, said component can be operated at a lower frequency (a longer wavelength) than prior art . The size reduction of the circuital components by means of the present technique contributes with other significant benefits: superconducting materials can become a cost-effective solution in the construction of said network elements due to size reduction; by using superconducting materials in the construction of transmission lines, resonators and filters, the insertion- loss is reduced and the quality factor of such devices is increased. By increasing the quality factor of resonators and filters in the transmitters and / or receivers of any telecommunication system an improved performance is achieved in several aspects: the signal to noise ratio is enhanced (i.e., the quality of the telecom system), and the frequency spacing between adjacent channels can be reduced. The adjacent channel spacing reduction implies a more efficient use of the available spectrum, such that telecom operators can increase their network capacities (a higher density of users in cellular telephone systems, a higher information rate and traffic density in either data, voice or video signal transmission) . Brief Description of the Drawings Figure 1 shows some particular examples of spacefilling curves. Figure 2 shows several configurations of conventional transmission lines of prior art, and some particular embodiments of SFC transmission lines. Figure 3 shows a set of space-filling curves known as SZ curves. Figure 4 shows a set of space-filling curves named as ZZ curves. Figure 5 shows a set of space-filling curves based on the Peano curve. Figure 6 shows a set of space-filling curves based on the Peano curve too. Figure 7 shows a set of space-filling curves based on the Minkowski curve. Figure 8 shows two examples of loop curves constructed by connecting several space-filling curves as curves in Figure 7. Figure 9 shows some particular cases of space-filling curves named as HilbertZZ curves. Figure 10 describes a particular use of a particular case of SFC curve following the spirit of the present invention. Figure 11 describes a particular embodiment of a SFC transmission-line. Figure 12 shows another particular embodiment where a SFC transmission line is formed by a series connection of four Hilbert curves. Figure 13 shows the use of a SFC to load a conventional transmission line. Figure 14 shows a modification of the embodiment in Figure 13 by including some capacitive gaps within the conventional transmission line. Figure 15 shows a modification of said embodiment in Figure 14 where the capacitance of the gaps is increased by means of additional conducting strips. Figure 16 describes the physical construction of a planar capacitor. Figure 17 shows an example of how the capacitance of the planar capacitor in Figure 16 can be increased. Figure 18 shows a two-port resonator in which the resonant element is a straight, half-wave microstrip transmission line, and the input and output ports are coupled with capacitive gaps at the edges of the resonant line. Figure 19 shows a two-port resonator similar to the one in Figure 1, but where the microstrip line is folded following a SFC pattern. Figure 20 is a microstrip filter comprising several edge-coupled, half-wave straight microstrip line resonators. Figure 21 is a filter made by capacitively coupling the edges of several resonators like the ones shown in Figure 19. Figure 22 is a detail of a ladder slow-wave line. Figure 23 is a detail of a ladder slow-wave line like the one in Figure 22, but substituting the straight, steplike strips in between the two parallel, handle-like strips, by strips following a SFC curve based on the Koch fractal curve. Figure 24 shows another example of slow-wave transmission line where the metal strip is impressed with several slots based on SFC curves. Figure 25 shows another example of slow-wave transmission line comprising a conducting strip, wherein such strip has been etched with a fractal-like motive generated after an IFS algorithm based on the fractal known as Siepinski Carpet. Figure 26 shows another use of an SFC curve in a co- planar transmission-line. Figure 27 shows a slow-wave guided structure comprising a conducting strip, wherein such strip has been etched with a fractal-like motive generated after an IFS algorithm based on the fractal known as Siepinski Carpet. Figure 28 shows another example of slow-wave guided structure where the central strip is impressed with a slot, wherein such slot is shaped as a fractal structure based on the Sierpinski Carpet. Figure 29 shows another example of slow-wave guided structure where the central part of the metallic strip is removed and several straight steps are impressed according to a fractal distribution of points with a fractal dimension smaller than one such as the Cantor Set, wherein said fractal distribution determines the spacing between the steps. Figure 30 shows the complementary version of the slow-wave structure in Figure 29 where the fractal staircase based on the Cantor Set is slotted in the central strip of the slow-wave guided structure. Figure 31 shows a hairpin filter. It is an evolution of a parallel-coupled, straight-line filter in which the line resonators are folded. Figure 32 shows two hairpin resonators using capacitive load at their edges to reduce the size of the microstip line. Figure 33 shows a hairpin resonator with a capacitance made with a SFC-shaped slot to maximize the capacitive coupling. Figure 34 shows an evolution of Figure 33, where SFC geometries are not only used to shape the slot of the capacitance, but also to shape the microstip jointing the electrodes of the capacitor. Figure 35 describes a parallel first order resonator formed by a central inducting strip connected in parallel with two adjacent capacitive gaps 19.4. As it is clear to those skilled in the art, the resonator can be used as a filter or part of a filter. Figure 36 describes a series first order resonator formed by a planar capacitor with a series connection to a planar inductor, wherein said capacitor is constructed for instance as described in Figure 16 and wherein said inductor is a conducting strip shaped as an SFC curve. As it is clear to those skilled in the art, the resonator can be used as a filter or part of a filter. Figure 37 shows another embodiment of a parallel planar resonator comprising an inducting strip connected in parallel to an SFC capacitor. As it is clear to those skilled in the art, the resonator can be used as a filter or part of a filter, and more than two stages of first order resonators can be used. Figure 38 shows an example of parallel planar resonator comprising a planar SFC capacitor including a SFC-shaped gap and an inductor connected in parallel constructed by means of a SFC strip. Figure 39 shows three examples of planar, two- dimensional, microstrip patch resonators formed by a fractal pattern, a one-dimensional repetition of a fractal pattern, or a two-dimensional repetition of a fractal pattern. Figure 40 shows a microstrip loop resonator shaped as a closed space-filling curve based on the Koch curve. Figure 41 shows two microstrip patch of space-filling perimeter based on the fractal Koch curve. Detailed Description of the Preferred Embodiments Figure 1 shows some particular examples (1.2-1.7) of space-filling curves. Curve (1.2) is made of 13 segments, curve (1.3) is made of 52 segments, curve (1.4) is made of 208 segments, curve (1.5) is made of 832 segments, curve (1.6) is made of 3328 segments and (1.7) is made of 13312 segments. Said curves can be constructed with an NMRCM algorithm and approximate the shape of the ideal Hilbert curve as it is described in the literature. Figure 2 shows several configurations of conventional transmission lines (prior art): a micro-strip (2.1), a strip-line (2.2), a co-planar line (2.3) and a parallel plate line (2.4) with their characteristic conducting strips (2.6), and a slot-line (2.5) characterized by the slot (2.12) between the two conducting or superconducting strips. In the right column, some particular embodiments of SFC transmission lines based on the SFC (1.4) are represented (micro-strip (2.7), strip-line (2.8), co- planar (2.9), parallel plate (2.10) and slot-line (2.11)). Figure 3 shows a set of space-filling curves known as SZ curves. The curves can be constructed by means of an NMRCM procedure from two sets of points based on curve (3.1) as it is described in several mathematics treatises. Notice that curves (3.2), (3.3), and (3.4) have been constructed with more than ten connected straight segments. Figure 4 shows a set of space-filling curves named as ZZ curves. The curves can be constructed by means of a characteristic IFS algorithm. Notice that curves (4.2), (4.3), (4.4) and (4.5) have been constructed with more than ten connected straight segments. Figure 5 shows a set of space-filling curves based on the Peano curve. The curves can be constructed by means of a characteristic IFS algorithm as it is described in the literature. Notice that curves (5.2), (5.3), and (5.4) have been constructed with more than ten connected straight segments. Figure 6 shows a set of space-filling curves based on the Peano curve. As it is clear to those skilled in this art of mathematics, the curves can be constructed by slightly modifying the characteristic IFS algorithm used in the construction of curves in Figure 5. Notice that curves (6.2), (6.3), and (6.4) have been constructed with more than ten connected straight segments. Figure 7 shows a set of space-filling curves based on the Minkowski curve. The curves can be constructed by means of a characteristic IFS algorithm. Notice that curves (7.2), (7.3), (7.4) and (7.5) have been constructed with more than ten connected straight segments. Figure 8 shows two examples of loop curves constructed by connecting several space-filling curves as curves in Figure 7. As it is clear to those skilled in the art of mathematics, a similar procedure can be applied to other space-filling curves as the particular cases described in figures 1 through 9. Figure 9 shows some particular cases of space-filling curves named as HilbertZZ curves. They are clearly defined as space-filling curves and they cannot be constructed after a simple IFS (or MRCM) algorithm. Figure 10 describes a particular use of a particular case of SFC curve following the spirit of the present invention. The Hilbert curve (1.5) is used to shape the characteristic strip of a microwave transmission line. The two tips of the curve form the input (10.2) and output (10.3) of the transmission line, that can be connected to other strips as for instance (10.4) and (10.6). Said strip based on the Hilbert curve (1.5) can be used to shape any of the well-known transmission-line configurations described in the prior art (drawings (2.1-2.5). according to the spirit and scope of the present invention. As it will be readily apparent to those skilled in the art, a Hilbert curve is shown here as a particular example but any other space-filling curves can be used within the spirit and scope of the present invention. Figure 11 describes a particular embodiment of a SFC transmission-line. The transmission line is terminated with either a short-circuit (11.3) or an open circuit (11.7). A one-port device is formed this way, wherein said device operates as a resonator, a capacitor or inductor depending on the operating frequency as it is clear to those skilled in the art. As it is apparent to those skilled in the art, a Hilbert curve is shown here as a particular example but any other space-filling curves can be used within the spirit and scope of the present invention. Figure 12 shows another particular embodiment where a SFC transmission line is formed by a series connection of four Hilbert curves based on the particular case (1.5), wherein said curves shape the characteristic strip or slot of any of the well known transmission-line configurations described in the prior art (drawings (2.1), (2.2), (2.3), (2.4) and (2.5)) according to the spirit and scope of the present invention. As it becomes apparent to those skilled in the art another different number of connected curves can be used instead of four to conveniently increase or reduce or the effective electrical length of the transmission line. The embodiment in Figure 12 can be terminated in the same way as described in Figure 11. Figure 13 shows the use of a SFC to load a conventional transmission line (13.2) . Any of the embodiments shown in Figure 11 can be used to load the line, and of course any other SFC curve as for instance those described in figures 1 through 9. The drawing in Figure 13 shows the characteristic strip or slot that is applied in the present invention to any of the well known transmission-line configurations as described in the prior art (drawings (2.1), (2.2), (2.3), (2.4) and (2.5)). The resulting device can be used for instance as a slow-wave line, resonator, or as a filter. Figure 14 shows a modification of the embodiment in Figure 13 by including some capacitive gaps (14.1) within the conventional transmission line. Figure 15 shows a modification of said embodiment in Figure 14 where the capacitance of the gaps is increased by means of additional conducting strips ((15.1), (15.2), (15.3) ) . Figure 16 describes the physical construction of a planar capacitor. The structure is formed by to metallic or superconducting plates (16.1) and (16.2) separated by a gap or slot (16.3), wherein said gap is shaped as an SFC curve. A particular case of a Hilbert curve (1.5) has been used here, but it is apparent to those skilled in the art that any other SFC (as for instance those described in figures 1 through 9) can be used within the spirit and scope of the present invention. Figure 16 presents an embodiment of planar SFC capacitance which can be used instead of inter-digitated capacitances in planar circuits. Said SFC capacitance is for instance composed by two co-planar metallic or superconducting strips, wherein said strips are separated by means of a slot, said slot being shaped as an SFC curve. Those skilled in the art will understand that the capacitance of this novel device can be controlled for instance by either adjusting the width or the length of the SFC slot (for example by adding more segments or by scaling the whole or part of the curve) . Prior art inter-digitated capacitances are widely used in planar circuits to provide high values of capacitive coupling between two metallic or superconducting patches or strips. These structures usually have a meander-shaped slot separating said two patches or strips. Often said strips or patches being mounted over a dielectric substrate; those skilled in the art will notice that the same conventional fabrications techniques can be also applied to the designs including the SFC slots disclosed in the present invention. One of the advantages of using the new SFC configuration claimed in this patent is that an even greater capacitance can be achieved by using a SFC-shaped slot. Said capacitances find many uses in planar circuits forming part of resonators, DC blocks, and other reactive elements. In the spirit of the invention, this increase in capacitance could also be achieved by using any other SFC, FSFC, fractal, Hilbert, SZ, ZZ, HilbertZZ, Peano, Minkowski or Sierpinski curve. Figure 17 shows an example of how the capacitance of the planar capacitor in Figure 16 can be increased. The length of the gap (16.3) is increased by connecting several SFC curves. Figure 18 (prior art) shows a two-port resonator in which the resonant element is a straight, half-wave microstrip transmission line (18.3), and the input and output ports are coupled with capacitive gaps (18.1) and (18.2) at the edges of the resonant line. Figure 19 shows a two-port resonator similar to the one in Figure 1, but where the microstrip line is folded following a SFC pattern (1.5). As pointed out in Figure 10, this efficiently packs the length of the resonant line in a small surface of the planar substrate. The input and output ports are coupled with capacitive gaps at the edges of the resonant line. Figure 19 shows an example of a microstrip line resonator where the line has been folded following the Hilbert curve of Figure 1. It is clear that other SFC, FSFC, fractal, Koch, SZ, ZZ, HilbertZZ, Peano, Minkowski or Sierpinski curves could be used instead (see examples in Figures 1, 3, 4,5,6,7,8 and 9), according to the spirit of the present invention. Said folded geometry efficiently packs the length of the resonant line. Those skilled in the art will notice that said geometry can be used to shape the strip of a micro-strip, strip-line, co-planar or parallel plate transmission line. Said strip can be constructed for instance with a metallic or superconducting material which can be deposited using well-known fabrication techniques over the surface of a dielectric substrate. Depending on the chosen configuration (strip-line, micro-strip, parallel-plate,..) the transmission line will obviously include other metallic or superconducting strips or ground-planes according to the description in Figure 2. Also, the input (19.1) and output (19.2) gaps are used to control the coupling of the source and load to the resonator in the same way as used in previous art well-known configurations of resonators. In another preferred embodiment, the resonator is directly connected to the input and output transmission lines instead of using a gap capacitance as described in drawings of Figure 10. One of the main advantages of the described inventions is the substantial saving in substrate space. Said saving is advantageous in many applications where volume and weight of the electronic equipment is critical, or when the substrate is expensive. In a third preferred embodiment, the resonator is made on a MMIC substrate using the conventional foundry techniques of MMIC fabrication. In that case, the resonator can be included in a multi-layer structure and can be connected or electromegnetically coupled with circuitry not contained in the layer of the said resonator. Those skilled in the art will recognize the possibility of making filters using several structures like the SFC-folded line described above by providing electromagnetic coupling among said structures. This electromagnetic coupling can be realized with capacitive- slot gaps, inductive coupling, or other techniques. Furthermore, the SFC-folded lines in said filters do not necessarily need to be at resonance at any of the frequencies falling within the passband of the filter. Figure 20 (prior art) is a microstrip filter comprising several edge-coupled, half-wave straight microstrip line resonators. Figure 21 is a filter made by capacitively coupling the edges of several resonators like the ones shown in Figure 19. Figure 22 (prior art) is a detail of a ladder slow- wave line. Instead of using a solid strip, this line uses a fine ladder pattern, whose features are much smaller than the free-space wavelength. This reduces the velocity of propagation in the transmission line. Figure 23 is a detail of a ladder slow-wave line like the one in Figure 22, but substituting the straight, steplike strips in between the two parallel, handle-like strips, by strips following a SFC curve based on the Koch fractal curve. The Koch SFC-shaped strips (23.3) connecting the two long and parallel narrow strips (23.4) provide and enhancement in the capacitance per unit length of the structure respect to what is achieved in a prior art structure using straight strips instead of the SFC-shaped ones presented herein. The high increase in capacitance per unit length is made with little change in the inductance per unit length of the structure, which is dominated by the effect of the two narrow, parallel strips. This increased capacitance provides a reduced velocity of propagation of the electromagnetic signals along the structure. In the spirit of the invention, this increase in capacitance could also be achieved by using any other SFC, FSFC, fractal, Hilbert, SZ, ZZ, HilbertZZ, Peano, Minkowski or Sierpinski curve that would not significantly alter the overall width of the structure nor the width of its two narrow, parallel strips. This type of line would not only be of use in a filter with straight transmission line resonators (like the one in Figure 20), the resonators in Figs. 19 and 21 could also be made out of slow-wave lines with SFC, FSFC, fractal, Hilbert, SZ, ZZ, HilbertZZ, Peano, Minkowski or Sierpinski features, further reducing their size for a fixed resonant frequency. Figure 24 shows another example of slow-wave transmission line where the metal strip is impressed with several slots based on SFC curves. Figure 25 shows another example of slow-wave transmission line comprising a conducting strip (25.2) (the metallic or superconducting part is shown in black) , wherein such strip has been etched with a fractal-like motive generated after an IFS algorithm based on the fractal known as Siepinski Carpet. The self-inductance of the strip is increased this way while the capacitance is kept high compared to other classical mechanisms due to the space-filling properties (fractal dimension) of the fractal-like shape. The electrical length of the transmission line is increased such that said slow-wave transmission line can be packed in a reduced space. Figure 26 shows another use of an SFC curve in a co- planar transmission-line. The characteristic central strip (26.3) of a co-planar line is separated from the ground strips (26.1) and (26.5) by two capacitive gaps (26.2) and (26.4) at both sides of the transmission line, wherein said gaps are shaped as an SFC curve (in this particular example a Hilbert curve) . A slow-wave transmission line is formed this way such that the length of the said transmission line is reduced compared to conventional co- planar transmission lines. Figure 27 shows a slow-wave guided structure comprising a conducting strip (27.2) (the metallic or superconducting part is shown in black) , wherein such strip has been etched with a fractal-like motive generated after an IFS algorithm based on the fractal known as Siepinski Carpet. The self-inductance of the strip is increased this way while the capacitance is kept high compared to other classical mechanisms due to the spacefilling properties (fractal dimension) of the fractal-like shape. The electrical length of the transmission line is increased such that said slow-wave transmission line can be packed in a reduced space. Figure 28 shows another example of slow-wave guided structure where the central strip is impressed with a slot (28.3), wherein such slot is shaped as a fractal structure based on the Sierpinski Carpet. Figure 29 shows another example of slow-wave guided structure where the central part of the metallic strip is removed and several straight steps (29.3) are impressed according to a fractal distribution of points with a fractal dimension smaller than one such as the Cantor Set, wherein said fractal distribution determines the spacing between the steps (29.3). Figure 30 shows the complementary version of the slow-wave structure in Figure 29 where the fractal staircase based on the Cantor Set is slotted in the central strip of the slow-wave guided structure. The arrangement of the velocity-reducing features along the resonator does not necessarily have to be periodic. Figure 27 shows a modified embodiment using a Sierpinski Carpet metallic or superconducting guiding structure. Note that the parallel, narrow strips along the edge of the resonator are maintained to obtain high inductance and low propagation velocity along the structure. Other non-periodic structures are shown in Figures 29 and 30, where a fractal-like distribution for the position of the strips (29.3) and (29.2) has been chosen to further increase the capacitance per unit length and further decrease the propagation velocity. Figure 31 (prior art) shows a hairpin filter. It is an evolution of a parallel-coupled, straight-line filter in which the line resonators are folded. Figure 32 shows two hairpin resonators using capacitive load at their edges to reduce the size of the microstrip line. Resonator (32.1) uses coupled-lines to realize such capacitance; Resonator (32.2) shows a resonator with a straight slot capacitance. Figure 33 shows a hairpin resonator with a capacitance made with a SFC-shaped slot to maximize the capacitive coupling. Figure 34 shows an evolution of Figure 33, where SFC geometries are not only used to shape the slot of the capacitance, but also to shape the microstip jointing the electrodes of the capacitor. Figure 35 describes a parallel first order resonator formed by a central inducting strip (35.2) connected in parallel with two adjacent capacitive gaps (35.4). As it is clear to those skilled in the art, the resonator can be used as a filter or part of a filter. Figure 36 describes a series first order resonator formed by a planar capacitor (36.2) with a series connection to a planar inductor (36.1), wherein said capacitor is constructed for instance as described in Figure 16 and wherein said inductor is a conducting strip shaped as an SFC curve. As it is clear to those skilled in the art, the resonator can be used as a filter or part of a filter. Figure 37 shows another embodiment of a parallel planar resonator comprising an inducting strip (37.1) connected in parallel to an SFC capacitor (37.4). The input and output ports of the resonator are (37.2) and (37.3). As it is clear to those skilled in the art, the resonator can be used as a filter or part of a filter, and more than two stages of first order resonators can be used. Figure 38 shows an example of parallel planar resonator comprising a planar SFC capacitor including a SFC-shaped gap and an inductor connected in parallel constructed by means of a SFC strip. Figures 36, 37, and 38 disclose a construction of several lumped and quasi-lumped resonators using SFC curves. The SFC-based capacitors as shown in Fig.16 are connected in series or parallel to other metallic or superconducting strips (36.1, 37.1), which can be adjusted in length to achieve the desired resonant frequency. Said metallic or superconducting strip used in conjunction with said SFC capacitor, can optionally be shaped as an SFC curve as shown in Fig.36 and Fig.38. In a preferred embodiment, said resonating structure can be integrated in the same plane as the characteristic strip of a micro- strip, strip-line, co-planar line or parallel-plate circuit. In another preferred embodiment, said resonating structure can be used as a stand-alone component packed, for instance, as a surface mounted device (SMD) . Those skilled in the art will notice that said stand-alone configuration can be also used in another preferred embodiment as being proximity coupled to a planar circuit either by mounting said resonator in the same plane as the circuit or in a different plane as done in flip-chip mountings. Figure 39 shows three examples of planar, two- dimensional, microstrip patch resonators formed by a fractal pattern (Sierpinski Carpet, (39.1)), a one- dimensional repetition of a fractal pattern (39.2), or a two-dimensional repetition of a fractal pattern (39.3). Figure (39.1) also shows an example of a possible use of these resonators, taking advantage of their dual resonant modes . Figure 40 shows a microstrip loop resonator shaped as a closed space-filling curve based on the Koch curve. As in the microstrip or stripline ring resonators, the degenerate modes in this resonator can be used in planar filters. Figure 41 shows a microstrip patch of space-filling perimeter based on the fractal Koch curve (41.1). To further reduce the resonant frequency of the structure, a hole with a SFC perimeter can be placed inside the patch as shown in Figure (41.2). Fig. 39 and Fig. 41 describe another preferred embodiment of a SFC and a fractal-based structure to construct a miniature resonator. A micro-strip or strip- line patch resonator is a solid flat island-like metallic or superconducting structure which is patterned in the same way as the strips of the microstrip and strip-line transmission lines described in Figure 2. We disclose here a new method of lowering the resonant frequency of such patch resonator by means of SFC and fractal-based structures. In a preferred embodiment the perimeter of the patch is shaped as an SFC or FSFC curve (41.1); optionally a centre hole with a SFC or FSFC perimeter (41.2) can be used to further reduce the resonating frequency. In another preferred embodiment, a structure based on a fractal surface pattern such as the Sierpinski Carpet can be used to reduce the resonant frequency (Fig.39). As it can be readily seen to those skilled in the art, the just disclosed fractal and SFC patch resonators (Fig.39 and Fig.41) can be also operated in a multi-mode configuration. That is, advantage can be taken of the several degenerate modes that resonate at the same frequency to implement a multi-pole filter with a reduced number of resonant structures. To couple the several degenerate modes a conventional technique is applied which consists on slightly perturbing the patch geometry (for instance but not limited to: cutting a corner, adding a notch or a small strip) . Multi-mode resonators can also be constructed with transmission line loops having adequate symmetries as readily known by those skilled in the art. SFC and FSFC loops as for instance those shown in Fig.8, Fig.15 and Fig.41 can be used to construct a multi-mode miniature resonator. The coupling among the degenerate modes is done using the techniques cited above. Another preferred embodiment of an SFC, fractal or FSFC network consists on depositing a resistive material strip over a dielectric substrate wherein said strip is shaped as an SFC, fractal or FSFC curve. In this particular embodiment, said curve do not form a closed loop and the two tips of the curve form the terminals of the resistor. As readily known by those skilled in the art, metallic bonds can be attached to said tips to form the input and output connecting points. The resistors can be packed in any of the well-known configurations described in the prior art (such as for instance an SMD component) or integrated in electric or microwave circuits in conjunction with other circuital components. The advantage of using the SFC and other geometries described in the present invention is that the size of the component is dramatically reduced, while increasing the resistance yet keeping the parasitic reactance of the component low compared to the prior art . Having illustrated and described the principles of our invention in a preferred embodiment thereof, it should be readily apparent to those skilled in the art that the invention can be modified in arrangement and detail without departing from such principles. We claim all modifications coming within the spirit and scope of the accompanying claims.

Claims: CLAIMS 1.- An electromagnetic transmission-line in which at least one of its parts is shaped as a space-filling curve (hereafter SFC) , being said SFC defined as a curve composed by at least ten connected straight segments, wherein said segments are smaller than a tenth of the operating free-space wave length and they are spatially arranged over a surface in such a way that none of said adjacent and connected segments form another straight segment, wherein none of said segments intersect to each other except optionally at the tips of the curve, and wherein the corners formed by each pair of said adjacent segments can be optionally rounded or smoothed otherwise. 2.- An electromagnetic transmission-line in which at least one of its parts is shaped as a fractal curve, being said fractal curve constructed after an Iterated Function System (IFS), a Multi Reduction Copy Machine (MRCM) or a Networked Multi Reduction Copy Machine (NMRCM) , wherein said IFS, MRCM and NMRCM algorithms comprise a characteristic set of affine linear transformations, being said transformations selected from the following: rotation, translations, scaling, skewing and mirroring, wherein said set of transformations are applied in a first stage to a set of points A0, comprising at least a curve, to obtain a set of points Al; in a second stage to said resulting set Al to obtain a set A2, and so on until a set An is obtained after as many stages as required to obtain a fractal curve of a physical length larger than a tenth of the operating wave-length. 3.- An electromagnetic transmission-line in which at least one of its parts is shaped as a fractal spacefilling curve (hereafter FSFC) , being said FSFC defined as a curve with a box-counting dimension larger than one, wherein such a box-counting dimension is computed as usual over the FSFC as the slope of the straight portion of a log-log graph, wherein such a straight portion is substantially defined as a straight segment over an octave of scales on the horizontal axes of the log-log graph. 4.- An electromagnetic transmission-line in which at least one of its parts is shaped either as a Hilbert or a Peano curve. 5.- An electromagnetic transmission-line in which at least one of its parts is shaped either as an SZ, ZZ, Dragon or HilbertZZ curve. 6.- An electromagnetic transmission-line in which at least one of its parts is shaped either as a Koch, Minkowski or Sierpinski curve. 7.- A slow-wave transmission line or electromagnetic guiding structure in which at least one of its parts is shaped as a SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claims 1, 2, 3, 4, 5, or 6. 8.- A slow-wave transmission line or electromagnetic guiding structure formed by the periodic repetition of a SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claims 1, 2, 3, 4, 5, or 6. 9.- A micro-strip transmission line comprising: (A) a metallic or superconducting ground-plane, (B) a metallic or superconducting strip parallel to said ground-plane, (C) an optional set of dielectric material slabs placed between the strip and the ground-plane, wherein at least a portion of said strip is shaped either as an SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claims 1, 2, 3, 4, 5, or 6. 10.- A strip-line transmission line comprising: (A) two parallel metallic or superconducting ground- planes, (B) a metallic or superconducting strip placed between said ground-planes, (C) an optional set of dielectric material slabs placed between said ground-planes, wherein at least a portion of said strip is shaped either as an SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, Minkowski, HilbertZZ, or Sierpinski curve as defined in claims 1, 2, 3, 4, 5, or 6. 11.- A co-planar transmission line comprising: (a) two metallic or superconducting ground-strips laying on the same plane, (b) a metallic or superconducting central strip lying on the same plane as said ground-strips wherein said strip is placed between said ground-strips , (c) an optional set of dielectric material slabs supporting said ground-strips and said central strip, wherein at least a portion of said central strip is shaped either as an SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claims 1, 2, 3, 4, 5, or 6. 12.- A coaxial transmission line comprising: (a) a metallic or superconducting shielding, (b) a central metallic or superconducting strip or wire placed within said shielding, (c) an optional dielectric material placed inside the shielding wherein at least a portion of said central strip or wire is shaped either as an SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curves as defined in claims 1, 2, 3, 4, 5, or 6. 13.- A parallel plate transmission line comprising: (a) two parallel metallic or superconducting strips, wires or plates, (b) an optional dielectric material placed between said strips wires or plates, wherein at least a portion of said parallel strips, wires or plates are shaped either as an SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claims 1, 2, 3, 4, 5, or 6. 14.- A dielectric wave-guide comprising: (a) a dielectric slab, (b) a dielectric strip etched over said slab with a dielectric permitivity larger than that of said slab, wherein at least a portion of said strips, is shaped either as an SFC, Fractal, FSFC, Hilbert, Peano, SZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claim 1, 2, 3, 4, 5, or 6. 15.- A slot-line transmission line comprising two metallic or superconducting strips laying on the same plane, wherein said strips are separated by a slot or gap shaped as a an SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claims 1, 2, 3, 4, 5, or 6. 16.- A distributed capacitor comprising a transmission line according to claims 1, 2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13 or 14 wherein said transmission line has an open circuit at one end, and the electrical length of said transmission line is smaller than a quarter of the operating guided wave lengths. 17.- A distributed capacitor comprising a transmission line according to claims 1, 2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13 or 14 wherein said transmission line has a short-circuit at one end, and the electrical length of said transmission line is larger than an odd number of a quarter of the operating guided wave lengths. 18.- A capacitor comprising two co-planar metallic or superconducting plates wherein at least part of the boundary between said plates is a gap shaped as a SFC, a FSFC or a fractal curve as defined in claim 1, 2 or 3. 19.- A capacitor comprising two co-planar metallic or superconducting plates wherein at least part of the boundary between said plates is a gap shaped as a Hilbert, Peano, SZ, ZZ, Dragon, HilbertZZ, Koch, Minkowski or Sierpinski curve. 20.- A distributed inductor comprising a transmission line according to claims 1, 2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13 or 14 wherein said transmission line has a short-circuit at one end, and the electrical length of said transmission line is smaller than a quarter of the operating guided wave lengths. 21.- A distributed inductor comprising a transmission line according to claims 1, 2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13 or 14 wherein said transmission line has an open-circuit at one end, and the electrical length of said transmission line is larger than an odd number of a quarter of the operating guided wave lengths. 22.- A distributed inductor comprising a metallic or superconducting strip shaped as an SFC, a FSFC or a fractal curve as defined in claim 1, 2 or 3, wherein said strip lays down on a plane, being said plane the one including the characteristic strip of either a micro- strip, a strip-line, a co-planar transmission line or an SFC capacitor. 23.- A distributed inductor comprising a metallic or superconducting strip shaped as a Hilbert, Peano, SZ, ZZ, Dragon, HilbertZZ, Koch, Minkowski or Sierpinski curve, wherein said strip lays down on a plane, being said plane the one including the characteristic strip of either a micro-strip, a strip-line, a co-planar transmission line or an SFC capacitor. 24.- A one-port distributed electromagnetic resonator comprising a transmission line according to claim 1, 2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13 or 14 wherein any of its ends is either short-circuited, open-ended, or connected to a reactive load and wherein the coupling is located at any point along said transmission-line. 25.- A two-port distributed electromagnetic resonator comprising a transmission line according to claim 1, 2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13 or 14 coupled by two input-output ports at any pair of points along the length of said transmission-line. 26.- A reactive element comprising a distributed resonator according to claim 24 or 25 wherein said resonator is operated at a frequency lower than the first resonant frequency of said resonator. 27.- A distributed electromagnetic resonator comprising a chain of transmission lines according to claim 1, 2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13 or 14 with a serial connection between adjacent transmission lines. 28.- An electromagnetic resonator comprising at least a distributed capacitor and a distributed inductor according to claims 16 or 17 and 20, 21, 22 or 23. 29.- An electromagnetic filter comprising at least a resonator according to claim 24, 25, 27 or 28. 30.- An electromagnetic filter comprising at least a reactive element according to claim 26. 31.- A microwave filter comprising a transmission line and at least a stub implemented as a transmission line according to claim 1, 2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13 or 14, wherein such stub is connected in parallel at a point of said transmission line. 32.- A microwave filter comprising a transmission line and at least a distributed capacitor according to claim 16 or 17. 33.- A microwave filter comprising a transmission line and at least a distributed inductor according to claim 20 or 21. 34.- A patch resonator in which at least one of its parts is shaped as a SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claim 1, 2, 3, 4, 5, or 6. 35.- A patch microstrip or stripline patch resonator in which at least part of its perimeter is shaped as a SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claim 1, 2, 3, 4, 5, or 6. 36.- A microstrip or stripline patch resonator having inner and outer perimeters in which at least part of said perimeters is shaped as a SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claim 1, 2, 3, 4, 5, or 6. 37.- A patch resonator containing a slot shaped as a SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claim 1, 2, 3, 4, 5, or 6. 38.- A patch resonator formed by the repetition of a SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claim 1, 2, 3, 4, 5, or 6. 39.- A patch resonator formed by the planar repetition of a SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claim 1, 2, 3, 4, 5, or 6. 40.- A planar resonator in which at least one of its parts is shaped as a SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve as defined in claim 1, 2, 3, 4, 5, or 6. 41.- A one-port distributed electromagnetic resonator comprising a resonator according to claim 34, 35, 36, 38, 39 or 40. 42.- A two-port distributed electromagnetic resonator comprising a resonator according to claim 34, 35, 36, 38 or 40. 43.- A reactive element comprising a distributed resonator according to claim 41 or 42 wherein said resonator is operated at a frequency lower than the first resonant frequency of said resonator. 44.- An electromagnetic filter comprising at least a resonator according to claim 41 or 42. 45.- An electromagnetic filter comprising at least a reactive element according to claim 43. 46.- A multi-mode patch resonator comprising at least a resonator according to claim 34, 35, 36, 38 or 40, wherein at least a portion of said patch is removed, slotted, or distorted electromagnetically to couple several degenerate resonant modes. 47.- A multi-mode loop resonator comprising a metallic or superconducting strip, wherein at least a part of said strip is shaped either as an SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve, wherein at least a portion of said loop is removed, slotted, or electromagnetically distorted to couple several degenerate resonant modes. 48.- A multi-mode loop resonator comprising a slotted loop impressed on a metallic or superconducting plane, wherein at least a part of said slot is shaped either as an SFC, Fractal, FSFC, Hilbert, Peano, SZ, ZZ, Dragon, Koch, HilbertZZ, Minkowski or Sierpinski curve, wherein at least a portion of said loop is removed, slotted, or electromagnetically distorted to couple several degenerate resonant modes. 49.- A resistor comprising at least a dielectric substrate and a strip made of a resistive material, being said strip shaped as an SFC, a FSFC or a fractal curve as defined in claim 1, 2 or 3. 50.- A resistor comprising at least a dielectric substrate and a strip made of a resistive material, being said strip shaped as a Hilbert, Peano, SZ, ZZ, Dragon, HilbertZZ, Koch, Minkowski or Sierpinski curve.

Inventors: COLLADO GOMEZ JUAN CARLOS, DUFFO UBEDA NURIA, O'CALLAGHAN CASTELLA JUAN MANU, PUENTE BALIARDA CARLES, ROZAN EDOUARD JEAN LOUIS, COLLADO GOMEZ, JUAN CARLOS, DUFFO UBEDA, NURIA, O'CALLAGHAN CASTELLA, JUAN MANUEL, PUENTE BALIARDA, CARLES, ROZAN, EDOUARD, JEAN LOUIS
Applicants: CALLAGHAN CASTELLA JUAN MANUEL, COLLADO GOMEZ JUAN CARLOS, DUFFO UBEDA NURIA, FRACTUS SA, PUENTE BALIARDA CARLES, ROZAN EDOUARD JEAN LOUIS, COLLADO GOMEZ, JUAN CARLOS, DUFFO UBEDA, NURIA, FRACTUS, S.A., O'CALLAGHAN CASTELLA, JUAN MANUEL, PUENTE BALIARDA, CARLES, ROZAN, EDOUARD, JEAN LOUIS
Application year: 2000
Main classification: H01P3
IPC codes: H01P1, H01P3, H01P7