OVERVOLTAGE PROTECTION

Abstract: An amplifier of differential type such as a comparator or operational amplifier has two input terminals (1, 3) which are formed by the base terminals of input, amplifying transistors (T1, T2) of for example npn-type. The collectors of the input transistors are connected to some supply voltage (VCC) through for example a current mirror circuit (T4, T5). The emitters of the input transistors are through a transistor (T3) connected as a current generator connected to another supply voltage (VEE) close to ground potential. The base-emitter-junction in the input transistors are protected by protective transistors (T6, T7) which are connected as diodes, the emitters and bases of which are connected to each other. The effective pn-junction in the protective transistors is then the junction between the base and collector which normally has a larger breakthrough voltage then the pn-junction between the base and emitter. A protection of the input terminals of the amplifier is thereby obtained which can in a simple way be accomplished in for example integrated circuits. Then, the protective transistors are made in substantially the same way as the input transistors and have substantially the same electrical properties as they.

Description: OVERVOLTAGE PROTECTION TECHNICAL FIELD The invention relates to protection of differential input terminals of amplifiers and comparators and in particular to an amplifier of differential type having protected input 5 terminals. BACKGROUND OF THE INVENTION AND STATE OF THE ART I many practically used circuits comprising an operational amplifier the voltage between the two input terminals of such an amplifier always is very close to zero due to the fact that feedback is used and that the gain of an operational amplifier is very high. In 0 contrast, a comparator is designed to provide an output signal representing the voltage between the two input terminals of the comparator and thus, in normal use in a circuit generally always some voltage exists between the input terminals of the comparator. However, the input voltage can due to the exterior circuits providing signals to the input terminals become too large what can destroy the comparator circuit. If the feedback for s an operational amplifier is not functioning properly such an amplifier can also be destroyed if the provided input voltage becomes too large. The reason of the feedback being non-operative can be that a large voltage is provided to the input at the same time as "slew-rate "-limiting is made on the output terminal of the operational amplifier or that the output terminal of the operational amplifier is connected to a too great load. o Therefore, protection circuits are required both for operational amplifiers and in particular for comparators. The latter ones obviously have not, in conventional circuits, a mechanism limiting the voltage between the input terminals. SUMMARY OF THE INVENTION It is an object of the present invention to provide a simple and efficient protection of 5 the input terminals of an amplifier of differential type. The two input terminals of a transistor based amplifier of differential type as considered herein are thus in the conventional way the base terminals of the input, active amplifying transistors. The base-emitter junctions in the input transistors are protected by transistors connected as diodes in which the emitters and bases are connected to each 0 other. The active pn-junctions in the protection transistors are then the junctions between base and collector which normally have a greater breakthrough voltage in the backward direction then the pn-junction between the base and the emitter. The protection transistors can advantageously be made in substantially the same way as the input transistors and have substantially the same electrical properties as them what makes it simple to 5 introduce the protection in an electronic integrated circuit. Thus, generally an amplifier of differential type is considered which comprises two amplifier transistors, the input terminals of the amplifier being directly connected to the bases of each of the amplifier transistors for receiving the input voltage, the difference of which is to be produced and/or amplified and is obtained as an output voltage on an output terminal of the amplifier. The output voltage thus represents the voltage between the input terminals. Preferably, the output terminal is directly connected to the collector of one of the amplifier transistors. For protection of the input terminals and in particular preventing that too strong 5 currents will flow through the amplifier transistors, protective diodes are connected directly in series with the emitter of each of the first transistors. Each of the protective diodes is connected to have the same direction or polarity as the diode formed by the pn- junction between the base and the emitter of the transistor to of which it is connected. Furthermore, the protective diodes are formed by protective transistors, the emitter and o the base of which are directly electrically connected to each other. Generally then, not using the terms "emitter" and "collector", directly in series with that one of the pn-junctions in each of the amplifier transistors which has the lowest breakthrough voltage in the backward direction a protective diode is connected having the same direction or polarity as the diode formed by the pn-junction of the first transistor s having the lowest breakthrough voltage. The protective diodes each comprise a protective transistor of the same polarity type as the amplifier transistors, which in a differential amplifier generally are substantially identical to other or at least have substantially identical electrical characteristics or properties. That one of the first and second pn- junctions in each of the protective transistors which has the lowest breakthrough voltage o in the backward direction is short-circuited by a direct electrical connection. The amplifier transistors and the protective transistors can all be npn-transistors of substantially the same kind or all be pnp-transistors of substantially the same kind. BRIEF DESCRIPTION OF THE DRAWINGS The invention will now be described as non limiting embodiments with reference to 5 the accompanying drawings in which: Fig. 1 is a circuit diagram of a simple transistor based differential amplifier of a previously known type, Fig. 2 is a simplified circuit diagram of the amplifier of Fig. 1 in which only some essential components are drawn, 0 Fig. 3 is a schematic cross sectional view of a vertical npn-transistor. Fig. 4 is a circuit diagram of a differential amplifier having protection of the input terminals of a previously known kind, Fig. 5a is a picture which illustrates the equivalence between a transistor, the base and collector of which are directly electrically connected to each other, and a diode, 5 Fig. 5b is a picture illustrating the equivalence between a transistor, the base and emitter of which are directly electrically connected to each other, and a diode, Fig. 6a is a circuit diagram of an amplifier according to Fig. 2 having protection of the input terminals, the protection being obtained by as transistors connected as diodes, Fig. 6b is circuit diagram similar to that of Fig. 6a for transistors of other polarities, and Fig. 7 is a circuit diagram of an amplifier according to Fig. 1 having the same protection of the input terminals as shown in Fig. 6a. DESCRIPTION OF PREFERRED EMBODIMENTS Hereinafter an amplifier circuit having some definite polarities of the components will be described. It is obvious to one skilled in the art that the amplifier circuit can be used with opposite polarities so that npn-transistors are replaced by pnp-transistors and vice versa, that the directions of a diodes are reversed, that positive voltages become negative and vice versa, that current directions are reversed, etc. , provided that components are used which in other respects have corresponding or similar electric properties. In Fig. 1 a circuit diagram of a common form of input stage is shown, the input stage being illustrated as a differential amplifier suited to be used in for example comparators or operational amplifiers. The two input terminals 1 , 3 of the circuit are constituted by the base terminals of two identical transistors Tl and T2 of for example npn-type as is shown in the figure. The emitters of the transistors Tl, T2 are connected to each other at an emitter node 5 and are there connected to the collector of a third npn- transistor T3 which is biassed by suitable voltages to work as a current source and thereby provides an emitter current to the input transistors Tl and T2. The emitter of the third transistor can as shown in the figure be connected to some supply voltage V EE , for example a negative voltage a little offset from ground potential or the ground potential itself. The collectors of the two first transistors Tl and T2, the very amplifying transistors or input transistors, are connected to a supply voltage V cc , for example a positive constant voltage, in some suitable way, for example as is shown in the figure through a current mirror circuit. The current mirror circuit comprises two pnp-transistors T4 and T5, the bases of which are connected to each other and the emitters of which are connected to the supply voltage V cc . The pnp-transistor T4 for the first input transistor Tl further has its base and its collector connected to each other so that it acts as a diode, whereas these two transistors T4 and T5 have their collectors coupled to the collectors of the respective input transistors Tl and T2. The important fact associated with the connection of the input transistors Tl and T2 to the drive voltage V cc is that the transistors T4 and T5 have an equivalent impedance and idling or no-load voltage (Thevenin-equivalent) so that the input transistors Tl and T2 work in their active region, i.e. they are not saturated, and thus the voltages from their collectors to their bases always are positive. Thereby the transistors T4 and T5 in the current mirror can be replaced by resistors coupled between the collectors of the transistors and the positive supply voltage V cc . A simplified embodiment of an input stage, shown partly schematically and comprising only the components essential in this context, are shown in Fig. 2. Here the transistor T3 is shown as a current generator II, whereas the collectors of the input transistors Tl and T2 are only shown connected to generally denoted connection nodes. The output signal of the two circuits shown in Figs. 1 and 2 is in principle the 5 collector current through either one of the input transistors Tl, T2. A voltage representing this current can for example be extracted or retrieved at the terminal 7 of the collector electrode of the second input transistor T2. When the voltage between the input terminals 1 , 3 is small, the two input transistors Tl, T2 are active and current flows through their emitter terminals to the common o emitter node 5. The current through these transistors are determined by the current source II or the transistor T3 respectively and is distributed among them so that more current will flow through the input transistor which has the highest voltage on its input terminal, i.e. on its base. When voltage between the input terminals becomes sufficiently large, sufficiently large being taken to mean that the voltage is equally to some V τ , s where V τ is proportional to the absolute temperature and V τ is about 26 mV at ambient temperature, the current through the input transistor, which has the lowest potential on its input terminal, can be neglected and the potential on the base or input terminal of the other input transistor is determined by the saturation current of this transistor. The voltage between the base and the emitter of this transistor is for saturation approximately o given by V BE = V τ -log(Iι/I s ), where Iι is the current generated by the current generator II and I s is the saturation current of the transistor. Suppose now that the voltage on the input terminal 3 of the second input transistor T2 is maintained constant while the voltage on the second input terminal 1 of the first input transistor Tl is successively lowered. The voltage through the first input transistor 5 Tl will then be lowered until the voltage of the emitter node is determined by the current of the current generator II and the saturation current I s of the input transistors. When the voltage is further reduced, the pn-junction between the base and emitter in the first input transistor Tl will be forwardly biassed to a smaller and smaller extent in order to then be reverse-biassed. When the voltage finally becomes sufficiently negative, current will 0 again flow through the emitter of the first input transistor Tl but now in an opposite direction depending on the breakthrough voltage of said pn-junction being exceeded. All of this current then passes out through the first input terminal 1, i.e. the base of the first input transistor Tl . The current is then no longer determined by the current source II but by the driving capability of the exterior voltage sources and by the resistances of the two 5 input transistors Tl and T2. In any case, the current can destroy the two input transistors Tl, T2 but perhaps primarily the first input transistor Tl in which the developed power becomes greatest. The voltage which an npn-transistor can allow between its emitter and base before the reverse-biassed pn-junction starts to conduct current varies between different manufacturing processes and different component layouts. For signal processing transistors usually this current is greater than about 6 V and smaller than about 10 V. Generally, a bipolar transistor consists of three regions which are located at each other in a row and which often comprise layers located on top of each other, made of semiconductor material having alternating polarities so that a middle region and two exterior regions exist. A bipolar transistor can then be npn-type or pnp-type. A connection to exterior circuits is provided from each region which can also be called an electrode. The middle region is called the base and the two exterior regions comprise the collector and the emitter respectively. If voltages are applied to the terminals of an npn- transistor so that V c > V b > V e for an npn-transistor, and to a pnp-transistor, so that V c < V b < V e , where V c , V b , V e are the potentials on the collector, base and emitter respectively of the transistors, and if a not too large current is supplied to the base which should also be positive for an npn-transistor and negative for a pnp-transistor, the current through the collector of the transistor is controlled by the supplied base current. Roughly, the collector current can be proportional to the base current. The constant of proportionality is called BF, "forward current gain" , also denoted by β. An arbitrary one of the two exterior regions of bipolar transistor could then be called the emitter whereas the other region then is the collector of the transistor. Usually however, the collector and emitter are defined so that the constant β of proportionality becomes as large as possible. For the same polarities of the applied voltages, if the transistor is turned around so that the collector will be located where the emitter previously was located, it is possible to measure a corresponding constant of proportionality or current gain factor BR, "reverse current gain" . Usually BF is much larger than BR. This fact depends on several optimizations of the layout or structure of the transistors, these optimizations considering among other things that it is desirable to have a BF which is as large as possible, i.e. one of the gain factors should be given the highest possible value. The value of BR has less importance. Usual values are BF = 50 - 100 and BR = 0.5 - 10. It is important to observe that an obvious condition of using a transistor in an amplifier circuit is that it has a current gain factor larger than one. The most common embodiment of an npn-transistor in integrated circuits is a vertical transistor, as illustrated by the cross-sectional schematic view of Fig. 3. In some outer material 11, having a low doping of the same type as the base, layers are provided which form the parts or regions of the transistor. The collector 13 is the lowermost layer having a doping opposite that of the outer material. Centrally in this lowermost layer another layer 15 is located forming the base and centrally in the base region a further layer 17 is located forming the emitter, so that in the centre of structure a layer sequence is obtained comprising, from the bottom and upwards, collector, base and emitter. The different regions extend at the exterior edges up to the surface of the structure for exterior electrical connection. Such a transistor is made so that the doping levels are decreasing in the order emitter-base-collector, i.e. the emitter region has a higher doping than the base region and the base region has a higher doping than the collector region. Furthermore, the base layer 15 is very thin at the centre of the structure and the collector layer is relatively thick. This contributes to the desired properties comprising a high current gain factor BF and good high frequency properties. The same properties also result in that the breakthrough voltage BV cb , when the collector-base-junction is reverse- biassed, becomes significantly higher than the breakthrough voltage BV eb , when the emitter-base-junction is reverse-biassed. In manufacturing processes which have been optimized therefor often the breakthrough voltage BV cb between collector and base is of the magnitude of order 50 - 120 V, which is to be compared to the breakthrough voltage BV eb of 6 - 12 V for the emitter-base-junction. Such manufacturing processes are used in applications which require that the circuits can stand high voltages, for example in circuits for audio amplifies, voltage converters, electronic circuits for vehicles, etc. A previously known way of protecting the input stage as described above comprises connecting resistors Rl , R2 at the input terminals in series with the base terminals of the input transistors Tl, T2 according to Fig. 3. Thereby the base currents are limited. Furthermore, diodes Dl , D2 can be connected between the emitters and bases of these transistors so that these diodes conduct in a direction opposite the base-emitter-diode in each transistor. Thus, when the backward voltage between emitter and base of one of the transistors Tl, T2 exceeds the forward voltage for the corresponding exterior diode Dl, D2 connected antiparallel, the forward voltage being about 0.6 to 1 V, the current will be conducted through the exterior diode instead of being conducted through the respective transistor. An advantage of such a circuit solution comprising protective components is that the transconductance of the input stage in normal operation is not effected by the added protective components. It is well known that in manufacturing integrated circuits, when in the manufacturing process only transistors are available, diodes are obtained by connecting the base and collector of a transistor to each other, see Fig. 5a. Due to the two pn-junctions existing in a transistor obviously also a component having a diode function is obtained in the case where the base and emitter of the transistor are connected to each other, see Fig. 5b. However, such a diode component is seldom used, since it gets worse properties for most applications compared to a diode obtained by connecting the collector and the base of a transistor to each other. However it appears, that by using a bipolar transistor in an unconventional way it is possible to obtain a protection of the input terminals of differential amplifiers as described above. As has been mentioned above, in a transistor in most cases a high current gain is desired. In the application described hereinafter this is not necessary. In Fig. 6a a principle circuit diagram of a differential amplifier is shown which is constructed substantially as the amplifier shown in Figs. 1 and 2 and which has protection of the input terminals. A more complete circuit diagram is shown in Fig. 7. This circuit solution has two npn-transistors T6, T7 connected between the emitters of the input transistors Tl, T2 and the common emitter node 5. These transistors have their base terminals connected to the respective emitter terminals so that only the base-collector- diode is used. They are connected so that the emitter in a normal operation of the amplifier has a higher potential then the collector-base, e.g. the base-collector-diode is forwardly biassed. If, in the same way as has been discussed above, the input voltage on the base 3 of the second input transistor T2 is maintained constant while the voltage on the other input terminal 1, i.e. the voltage on the base of the first input transistor Tl, is gradually reduced, again firstly the current through the first transistor is lowered down to a zero. After some further reduction of the input voltage current will flow "backwards" in the direction from the emitter to the base in the first transistor Tl but now it will start to flow until the voltage between the node 5 and the input terminal 1 exceeds the sum of the breakthrough voltage BV eb between the emitter and base of the transistor Tl and the breakthrough voltage BV ce between the collector and emitter of the protective transistor T6. The breakthrough voltage BV ce between the collector and the emitter in a transistor is considerably, i.e. many times, larger than the breakthrough voltage BV eb between the emitter and base in the same transistor and is further of the same magnitude of order as the breakthrough voltage BV cb between the collector and base, as has been defined above. In the protected circuit solution according to Fig. 4 the current surge in the input transistor Tl occurs already when the voltage between the node 5 and the input terminal 1 exceeds the breakthrough voltage BV eb between the emitter and the base of the input transistor. In Fig. 6b a principle circuit diagram of a differential amplifier similar to that of Fig. 6a in which instead npn-transistors are used both as amplifying or active elements and as protective elements. This circuit operates in basically the same way as the circuit illustrated in Figs. 6a and 7. The advantage of the circuit solution according to Figs. 6a and 7 or Fig. 6b is thus that the circuit can stand voltages which are many times higher compared to the case having no protective components. Compared to the known circuit solution according to Fig. 4 two advantages exist. In the known solution a current passes through the protective components Rl, R2, Dl, D2, when the protection becomes operative. Such a non- controlled current can among other things result in overheating. This is not the case for the solution according to Figs. 6a and 7. Furthermore, resistors are often not suited to be integrated in monolithic integrated circuits, either due to the fact that the manufacturing process in itself is not suited for manufacturing resistors or due to the fact that they occupy a too large area on a circuit plate. In integrated circuits resistors are longer the larger resistance they have. Since the widths of the resistors are not allowed to be smaller than a definite smallest measure determined by mask production, optical resolution, etc. and the resistance then is determined by the ratio of the length and the width, resistors having high resistance values obtain a great length and thereby large areas. In the protective circuit according to Fig. 4 the power generation in the resistors Rl , R2 can become significant in the case where the other components in circuits, not shown, feeding the input terminals of the amplifier circuit allow it. The transistors T6, T7 connected as diodes in the circuit according to Figs. 6a, 6b and 7 influence the transconductance of the differential amplifier. This can be an advantage or disadvantage. Thus, in some previously known circuits resistors can be used connected at the positions of the protective transistors T6, T7 to lower the transconductance .

Claims: CLAIMS 1. An amplifier of differential type comprising two first transistors, each first transistor having an emitter, a base and a collector, and input terminals directly connected to the bases of each of the first transistors for receiving input voltages and an output terminal for providing an output voltage representing a voltage between the input terminals, characterized by protective diodes connected directly in series with the emitter of each of the first transistors, each of the protective diodes connected to have the same direction or polarity as the diode formed by the pn-junction between the base and the emitter of the first transistor to the emitter of which the protective diode is connected, and each of the protective diodes comprising a protective transistor, the emitter and the base of which are directly electrically connected to each other. 2. An amplifier according to claim 1, characterized in that the output terminal is directly connected to the collector of one of the first transistors. 3. An amplifier according to any of claims 1 - 2, characterized in that the first transistors and the protective transistors all have substantially the same electrical properties. 4. An amplifier of differential type comprising two first transistors of one polarity type, each first transistor having an emitter, a base and a collector, a first pn-junction existing between the base and the emitter and a second pn-junction existing between the base and the collector, and input terminals directly connected to the bases of each of the first transistors for receiving input voltages and an output terminal for providing an output voltage representing a voltage between the input terminals, characterized in that directly in series with that one of the first and second pn-junctions in each of the first transistors which has the lowest breakthrough voltage in the backward direction a protective diode is connected having the same direction or polarity as the diode formed by the pn-junction of the first transistor having the lowest breakthrough voltage, the protective diode comprising a protective transistor of the same polarity type as the first transistors, each protective transistor having an emitter, a base and a collector, a first pn- junction existing between the base and the emitter and a second pn-junction existing between the base and the collector, and that that one of the first and second pn-junctions in each of the protective transistors which has the lowest breakthrough voltage in the backward direction is short-circuited by a direct electrical connection. 5. An amplifier according to claim 4, characterized in that the output terminal is directly connected to the collector of one of the first transistors. 6. An amplifier according to any of claims 4 - 5, characterized in that the first transistors and the protective transistors all have substantially the same electrical properties. 7. An amplifier according to any of claims 4 - 6, characterized in that the pn- junction in the input transistor between the base and the emitter has a lower breakthrough voltage than the pn-junction between the base and the collector. 8. An amplifier according to any of claims 4 - 7, characterized in that the first transistors and the protective transistors all are npn-transistors of substantially the same kind, the emitters and bases of each of the protective transistors being directly electrically connected to each other. 9. An amplifier according to any of claims 4 - 7, characterized in that the first transistors and the protective transistors all are pnp-transistors of substantially the same kind, the emitters and bases of each of the protective transistors being directly electrically connected to each other.

Inventors: STENSTROEM HELGE, STENSTROEM, HELGE
Applicants: ERICSSON TELEFON AB L M, TELEFONAKTIEBOLAGET LM ERICSSON (PUBL)
Application year: 2000
Main classification: H03F3
IPC codes: H03F1, H03F3