BASE STATION, BASE STATION MODULE AND METHOD FOR DIRECTION OF ARRIVAL ESTIMATION

Abstract: The invention relates to a base station for a radio communications network. In order to be able to enhance the resolution for a direction of arrival estimation, the base station comprises: a first phasing network (31) for forming beams (B1-B4) for fixed reception angles; a second phasing network (33) for co-phasing and summing the signals of at least two neighbouring beams (B2, B3), thus forming a beam (B2-3) for a reception angle in-between at least those two neighbouring beams (B2, B3), and for scaling each resulting beam (B2-3) with a predetermined factor; and means for estimating the direction of arrival in the uplink from the beams (B1-B4, B2-3) provided by the first and the second phasing network (31, 33). The invention equally relates to a corresponding method and to a base station module comprising such a first and second phasing network.

Description: Base station, base station module and method for direction of arrival estimation FIELD OF THE INVENTION The invention relates to a base station for a radio communications network, a module for such a base station and a method for enhancing the angular resolution in the estimation of the direction of arrival of signals in the uplink in a base station of a radio communications network. BACKGROUND OF THE INVENTION It is known from the state of the art to provide base stations with smart antenna arrays which enable the output of fully steerable downlink beams. When employed for a user specific digital beamforming, a beamformer of such a smart antenna array is e.g. able to weight phase angle and/or amplitude of the transmitted signals in a way that the direction of the beam is adapted to move along with a terminal through the whole sector of coverage of the antenna array. In order to be able to move a downlink beam according to the movement of a terminal, the base station has to determine the direction in which the terminal can be found. This can be achieved by estimating the azimuth direction of arrival of the uplink signals received by the base station from the respective terminal. For receiving uplink signals, base stations often employ a fixed beam reception system, the fixed beams being evaluated for estimating the direction of arrival of the uplink signals. For illustration, figure 1 shows an example of an architecture in a base station used for the processing of signals from a single user for estimating the direction of arrival (DoA) . The part of the base station depicted in Figure 1 comprises an uplink digital beam matrix 11 connected at its inputs to a uniform linear antenna array (ULA) with eight receiver antennas (not shown) . The output of the uplink digital beam matrix 11 is connected via means for standard RAKE processing 12 to means for estimating the direction of arrival of uplink signals 13. The means for estimating the direction of arrival 13 are connected on the one hand to further components of the base station that are not shown. On the other hand, they are connected to processing means 14 suited for spreading and weighting of signals . The processing means 14 receive as further inputs signals from means for download bit processing 15 and output signals to means for user-specific digital beamforming 16. The outputs of the means for user-specific digital beamforming 16 are connected to eight transmit antennas (not shown) . The means for standard RAKE 12, for estimation of the DoA 13, for downlink bit processing 15 and the processing means 14 are used for digital base-band processing. Signals entering the base station via the receive antennas are first processed in the digital beam matrix 11. The digital beam matrix 11 is an MxM matrix, where M is the number of antenna elements, i.e. M = 8 in the described example. The digital beam matrix 11 generates from the received signals fixed reception beams in eight different directions. With the digital beam matrix 11 and the uniform linear antenna array (ULA) , orthogonal beams (butler matrix) or an arbitrary set of non-orthogonal beams can be generated. The generated beams are input to the means for standard RAKE 12. After a processing on the chip level by the means for standard RAKE 12 , the beams are evaluated in the means for estimation of the direction of arrival 13 in order to be able to determine the best direction for transmission of downlink signals. The direction of arrival of the uplink signals can be estimated by simply measuring the power from each beam. In particular, the power in the pilot symbols in the channel estimate can be determined. The beam direction of the beam with the highest uplink power, averaged over fast fading, is considered as the direction of arrival, to which the downlink beam is to be directed. Alternatively, the direction of arrival can be estimated with any other known method for determining the direction of arrival in the beam space. The means for estimation of the direction of arrival 13 provide the processing means 14 with power control and weight information for forming the downlink beams corresponding to the determined direction of arrival . In addition, further elements in the means for estimation of the direction of arrival 13 forward soft bits, including the data signals transmitted by the terminal, to the components not depicted in the figure . Hard bits constituting signals that are to be transmitted from the network to the terminal are processed, e.g. encoded, by the means for downlink bit processing 15 and forwarded to the processing means 14. The processing means 14 are able to spread and weight those signals according to the information received from the means for estimation the direction of arrival 13. The thus processed signals are transmitted to the means for user-specific digital beamforming 16 which transmit the signals via the transmit antennas in a downlink beam directed to the determined direction of arrival of the uplink signals. With this method, the estimation of the uplink direction of arrival is based on a rough resolution grid in the form of the fixed beams. That means, even though in the downlink the transmission beam can be steered continuously with arbitrary resolution, the accuracy of the downlink beamforming is limited to the uplink beam spacing. This accuracy is not adequate for downlink beam steering, if the number of beams is equal to the number of columns in the smart antenna array. Even if the direction of arrival resolution is improved as the number of reception beams is increased by increasing the number of receive antennas, the angular resolution is not adequate with 4-8 beams/antennas. In the uplink, the angular resolution is approximately 30° with 4 beams and approximately 15° with 8 beams. Figures 2a-d show this angular distribution of the fixed uplink beams for different constellations. Figure 2a is a diagram with the amplitude beam pattern over the azimuth angle in degrees of four orthogonal beams resulting from a 4-antenna array. Figure 2b is a diagram with the corresponding amplitude beam pattern of eight orthogonal beams of a 8-antenna array. In contrast, figure 2c is a diagram with the amplitude beam pattern of four non- orthogonal beams of a 4-antenna array and figure 2d a diagram with the amplitude beam pattern of eight non- orthogonal beams of a 8-antenna array. Alternatively to basing the estimation of the direction of arrival on the power of the fixed beams, the direction of the downlink beam can be selected by transforming the channel estimates back to the element domain. To this end, the beamformed signals are multiplied by an inverted digital beam matrix to obtain the element space signals. Then, any known direction of arrival techniques is used in the element space. However, for practical implementations this method leads to an excessive amount of computations. SUMMARY OF THE INVENTION It is an object of the invention to provide a base station, a base station module and a method which allow for a simple enhancement of the angular resolution in the estimation of the direction of arrival of uplink signals. This object is reached on the one hand with a base station for a radio communications network, comprising a first phasing network for forming beams for fixed reception angles out of signals provided by a receive antenna array and for outputting the signals constituting said beams; a second phasing network for co-phasing and summing the signals provided by the first phasing network for at least two neighbouring beams, thus forming a beam for a reception angle in-between the at least two neighbouring beams, and for scaling amplitude and/or power of each resulting beam with a predetermined factor; and means for estimating the direction of arrival in the uplink from the beams provided by the first and the second phasing network. On the other hand, the object is reached with a method for enhancing the angular resolution in the estimation of the direction of arrival of signals in the uplink in a base station of a radio communications network, comprising: receiving uplink signals with a receive antenna array of the base station; forming first beams for fixed angles of arrival out of the received signals in a first phasing network and outputting the signals constituting said beams; forming at least one composite beam in-between at least two neighbouring ones of the first beams in a second phasing network by co-phasing and summing the signals belonging to the neighbouring beams and by scaling amplitude and/or power of each resulting composite beam with a predetermined factor; and estimating the direction of arrival of the received signals based on the first beams and the composite beams. The object is equally reached with a base station module for a base station comprising such a second phasing network. The invention proceeds from the idea that a finer angular spectrum can be achieved by further processing the already beamformed uplink signals, which present a relatively rough angular spectrum. The finer resolution is achieved by simply applying multiplications and summings on the present fixed beams, followed by a subsequent scaling. A main advantage of the method, the base station and the base station module according to the invention is therefore the simplicity with which a finer angular resolution for the estimation of the direction of arrival of uplink signals is achieved. The estimated direction of arrival is used in particular for forming a downlink beam to be transmitted in said direction. Preferred embodiments of the invention become apparent from the subclaims . A receive antenna array employed for receiving uplink signals from a terminal and for providing the received signals to the first phasing network of the base station can be comprised by the base station of the invention or form an supplementary part of the base station. The same applies for a transmit antenna array. The first phasing network can be suited for forming orthogonal or non-orthogonal beams as fixed reception beams . Preferably, the first phasing network is moreover suited to form four or eight of such beams, depending on the number of receive antennas from which it receives uplink signals. However, any other number of receive antennas and to be formed beams can be chosen as well. In an advantageous embodiment of the base station and the method of the invention, co-phasing and summing of the signals of two neighbouring beams provided by the first phasing network is carried out for all neighbouring beams formed by the first phasing network. Accordingly, the total number of formed beams is twice minus one the number of the original beams formed by the first phasing network. Therefore, the resolution of the azimuth reception angle is doubled. The power and/or the amplitude of the composite beams resulting from the co-phasing and summing should be scaled according to the power and/or amplitude of the original beams, in order to make the composite beams comparable to the first beams for determining the direction of arrival. To this end, the composite beams can be scaled in a way that equal gains are achieved for all beams. The scaling factors can also be can also be selected so that the signal-to-noise ratio (SNR) for each beam is equal in case that the same signal is arriving to each beam. Alternatively, the scaling factors can be selected so that the signal-to-interference- and-noise ratio (SINR) for each beam is equal in case that the same signal is arriving to each beam. In case the composite beams are formed exactly in the middle of two neighbouring orthogonal beams, with four original orthogonal beams the scaling factor can be set to a value which compensates the loss of 0.67 dB for all composite beams and with eight original orthogonal beams to a value which compensates the loss of 0,86 dB, in order to obtain equal gains for all beams. In the case of four orthogonal beams, in order to compensate the loss of 0.67 dB, the power correction factor is 16/13.7 = 1.1679, while the amplitude correction factor is 4/ I3.7 = 1.0807. For achieving an even finer tuning of the angular resolution with the base station/base station module and by the method according to the invention, the signals of neighbouring original beams are multiplied by different predetermined factors before co-phasing and summing. Preferably, one factor is greater than 1 and the other factor smaller than 1. This way, the composite beam or beams are not necessarily placed at an angle exactly in the middle of the two neighbouring beams but can be shifted arbitrarily to any angle between the two original beams. In this case, the scaling factor that has to be applied on the formed composite beams depends in addition on the factors used for multiplying the amplitudes. The proposed fine tuning can be used in particular for generating several beams at different angles in between two original neighbouring beams by multiplying them with different sets of factors. Accordingly, any desired angular resolution can be obtained for estimating the direction of arrival in the uplink. The estimation of the direction of arrival in the uplink is preferably based on an evaluation of the power of the beams provided by the first and the second phasing network. The first and the second phasing network can be analogue phasing networks, but preferably they are digital phasing networks in which a complex valued weight vector represents each beam in the digital domain. Such digital phasing networks are advantageously formed by a digital beam matrix DBM. In a digital phasing network, complex weights can be stored. The complex weights are then applied to incoming signals for forming the desired beams. The complex weights of the first digital phasing network can be predetermined in any suitable manner so they are suited to form the predetermined number of beams at the predetermined angles . The complex weights of the second digital phasing network are determined in a way that the beams provided by the first phasing network are co- phased and summed in the second digital phasing network when applying the complex weights to the corresponding signals. In the digital domain, the co-phasing of neighbouring beams can be achieved by rotating the phase angle of at least one of the vectors representing two neighbouring beams. In the case of four orthogonal original beams, the phase angle of the vector representing the first of two neighbouring beams can e.g. be rotated by 0 and the phase angle of the vector representing the second of the two neighbouring beams by +3π/4 or -3π/4, depending on which beam was selected as first and which as second beam. In the case of signals received from an antenna array with eight antennas, formed into eight orthogonal beams, the phase angle of the vector representing the first of two neighbouring beams can e.g. be rotated by 0 and the phase angle of the vector representing the second beam by +7π/8 or -7π/8. The rotated vectors of the two neighbouring beams are then summed, thus forming a single vector. This single vector represents a single composite beam in the middle of the two original neighbouring beams . Also the multiplication of different neighbouring beams with different factors for fine tuning can be realised by multiplying the amplitudes of the corresponding vectors with different factors before rotating and summing. The method and the base station according to the invention can also be used for estimating the angular spreading of signals impinging at the base station. For example, after finding the DOA with largest average power the corresponding power is measured also from both adjacent beams. As described above, the increment of the direction angle from one beam to the adjacent beam can be set to be arbitrarily small. If the averaged power of the adjacent beam is above a pre-set threshold the number describing the angular spread is increased by the number corresponding to the angular increment between the two adjacent beams. The threshold can be also adaptive. For instance, the angular aperture of the entire sector is scanned and an average value for signal strength is obtained which depends on the desired signal, the interference scenario and the particular radio environment . The level of the desired signal is then compared to the averaged value describing the entire sector. If the desired signal exceeds the threshold the signal power of the next beam is then calculated. This process is repeated as long as the power level of the desired signal is above the threshold. Thus the angular spread (AS) is directly proportional to the number of beams in which the averaged power of the desired signal is above the threshold and to the angle interval between two adjacent beams: AS = N D where N equals the number of adjacent beams in which the desired signal power is above the threshold and D is the angle increment of neighbouring beams. For example, in case of 8 original beams and 7 mid-beams the angle increment D is approximately 7.5 degrees. If the signal power exceeds the threshold in three consecutive beams the angular spread is 22.5 degrees assuming the same angle increment D from beam to beam. It is also noted that the angle increment D may vary from beam to beam which is the preferred case in orthogonal beams. If the signal power exceeds the threshold in three consecutive beams the angular spread is 22.5 degrees . The proposed base station, base station module and method are particularly suited for an employment with WCDMA (wideband code division multiplex access) and EDGE (enhanced data rate for GSM evolution; GSM: global standard for mobile communication) . BRIEF DESCRIPTION OF THE FIGURES In the following, the invention is explained in more detail with reference to drawings, of which Fig. 1 shows the architecture in a base station for the processing of uplink signals from a single terminal ; Fig. 2a shows orthogonal beams of a 4-antenna array; Fig. 2b shows orthogonal beams of an 8-antenna array; Fig. 2c shows non-orthogonal beams of a 4-antenna array; Fig. 2d shows non-orthogonal beams of an 8-antenna array; Fig. 3 shows components of a base station according to the invention; Fig. 4 illustrates the forming of complex weights in the first digital phasing network; Fig. 5a shows a power beam pattern with one beam generated according to the method of the invention; Fig. 5b shows an amplitude beam pattern with three beams generated and scaled according to the method of the invention for a 4-antenna array; Fig. 6a shows an amplitude beam pattern with seven beams generated according to the method of the invention for an 8-antenna array; Fig. 6b shows an amplitude beam pattern with seven beams generated according to the method of the invention for an 8-antenna array with fine tuning; Fig. 7a shows an exemplary power distribution over 8 original beams ; and Fig. 7b shows an exemplary power distribution over 8 original and 7 composite beams generated according . to the invention in between the original beams . DETAILED DESCRIPTION OF THE INVENTION Figures 1 and 2a-d have already been described with reference to the background of the invention. Figure 3 depicts elements of a base station according to the invention that are used in a method according to the invention. In the base station of figure 3, a 4-antenna array is employed as receive antenna array. Each antenna Ant1-Ant4 is connected via a low noise amplifier LNA to a digital beam matrix DBM 31, which forms a digital phasing network and has stored complex weights. The digital beam matrix corresponds to the uplink digital beam matrix 11 in figure la, except that the digital beam matrix 31 of figure 3 is a 4x4 instead of a 8x8 matrix. A calibration unit 32 has access to the low noise amplifiers LNA. The digital beam matrix 31 has an output line for each of four beams B x to B 4 . The output lines for beams B 2 and B 3 are branched off and fed to a second digital phasing network 33. Also in the second digital phasing network 33 complex weights are stored. The second digital phasing network 33 has an output for a further beam The antenna elements Antl-Ant4 of the receive antenna array receive uplink signals from a terminal, the signals entering the antenna array from a certain direction depending on the present location of the terminal. The signals received by the antennas Antl-Ant4 are amplified in the low noise amplifiers LNA, the low noise amplifiers LNA being calibrated by the calibrating means 32 in a way that the transmission line from antenna elements Antl-Ant4 to the digital beam matrix 31 can be assumed to be identical . In the digital beam matrix 31, four orthogonal fixed reception beams B 1 -B 4 corresponding to those shown in figure 2a are formed by applying the suitably selected and stored complex weights to the received signals. The power or the amplitude of each beam indicates the strength of reception with a certain reception angle. The beams are output and fed to means for estimating the direction of arrival, as indicated e.g. in Figure 1. Two neighbouring beams B 2 and B 3 are fed in addition to the second digital phasing network 33. The second digital phasing network 33 performs a co-phasing and subsequent summing of the two beams B 2 , B 3 by applying the further complex weights to the signals belonging to the beams B 2 , B 3 . These complex weights are selected such that they cause a co-phasing and summing of the received beams received from the first digital phasing network 31. The result of the application of the complex weights is therefore a response in a direction in the middle between the directions of the two original beams B 2 , B 3 . The amplitude and the power of this composite beam B 23 , however, is somewhat reduced compared to the original beams B 2 , B 3 , when assuming the same signal strength in all three directions. When the amount of the reduction is known, however, the composite beams can be scaled so that the relative gain of the generated beam B 23j can be used in the means for estimating the direction of arrival for taking into account an additional azimuth angle. It is now explained with reference to Figure 4 how the scaling factor can be obtained for orthogonal beams of the 4-antenna array used in the base station of figure 3. Co-phasing of two adjacent beams can be achieved by co- phasing the complex valued weight vectors representing two neighbouring beams in the digital beam matrix 31 in the digital domain. The vector bi for beam Bi is obtained by summing the elements a k of the corresponding array response vector a : N *, =Σ Σ , Figure 4 illustrates in vector form how a digital beam matrix 31 used for generating four orthogonal beams B- L -B 4 determines complex valued weight vectors for beams B 2 and B 3 . Given a 4-beam digital beam matrix, the elements of the corresponding vector are added for beam B 2 , while the phase angle is rotated from one element to the next by 45°, as shown on the left hand side of figure 4. The resulting vector is b 2 = 1 + 2,414j. Similarly, the signals from the antenna elements are added for beam B 3 , but here the phase angle is rotated from one element to the next by -45°, as shown on the right hand side of figure 4. The resulting vector in this case is b 3 = 1 - 2,414j. Beam B 2 and beam B 3 are represented in the digital domain by these vectors b 2 and b 3 . The output of the first digital phasing network 31 can be co-phased by rotating the phase angle of beam B 2 or beam B 3 or both. Here, the phase angle of beam B 3 is rotated by 3π/4 to co-phase with beam B 2 . After co-phasing, the beams are summed, leading to a composite beam B 23 represented by b 2 _ 3 = b 2 +b 3 = 2+4 . 83j = 5 . 23 exp ( j 3π/8 ) . While the power of the four beams B x to B 4 output by the digital beam matrix 31 is 16, the power of the resulting beam B 23 is 0.5* (5.23) 2 = 13.7. Thus, the loss compared to the original beam is 13.7/16 = 0.67 dB . The knowledge of this loss enables a scaling of a beam generated in the middle of two fixed beams so that the relative gain of the generated beam is known and can be used for estimating the direction of arrival . The scaling factors are stored as well as the required complex weights. For other kinds of digital beam matrices the scaling factors are determined analogously. With an 8-antenna array and a digital beam matrix forming 8 non-orthogonal beams for example, the outputs for the two centre beams, B 4 and B 5 , are b 4 =l+5.03j and b 5 =l-5.03j. After co-phasing the two beams B 4 , B 5 by rotating B 5 by 7π/8, the composite beam B 45 is represented by b 45 = b 4 +b 5 = 2+10.05j = 10.25 exp(j7π/l6), the power being 52,5 as compared to 64 for the original beams B 1 -B 8 . Therefore, the loss in the antenna gain in this case is 52.5/64 = 0.86 dB for an 8-beam digital beam matrix. Instead of two adjacent beams, also more beams can be co- phased and summed to obtain mid-beams . Figure 5a is a diagram of the power beam pattern obtained by the base station of figure 3 without scaling in case of orthogonal Butler beams. The power is depicted over the azimuth angle from -100 to 100. As can be seen in the diagram, the power of the four original beams B x to B 4 is 16, while the power of the composite beam B 23 is 13.7, in line with the above calculation of the scaling factors. Figure 5b shows a diagram with the amplitude beam pattern of four original beams and three composite beams in case of non-orthogonal beams, where the beams are roughly scaled with corresponding scaling factors. The composite beams B x 2 , B 23 , B 34 have been formed between each existing pair of neighbouring original beams Ε> 1 / ~ B 2 I B 2 /B 3 and B 3 /B 4 . It becomes apparent from this figure that the direction of arrival resolution can be doubled by introducing a composite beam in between all neighbouring original beams. In another embodiment of the method according to the invention, a further increase of the angular resolution can be obtained. The above described embodiment applies only phase shifts to the original beams, which provides one additional beam exactly between two neighbouring beams . Providing such generated composite beams is not sufficient, if there is a need for fine tuning the directions of the composite beams. In order to be able to achieve a finer resolution, complex weights causing phase shifts and amplitude adjustments to the received beams are applied for neighbouring beams. This way, a composite beam can be directed into any desired direction. Figures 6a and 6b illustrate the difference between beamforming by phase shifting only and beamforming by phase shifting and an additional adjustment of the amplitudes of the original beams . Figure 6a is a diagram of the amplitude beam pattern from a 8-beam digital beam matrix forming 8 orthogonal beams B (i=l to 8) . The additional composite beam pattern for seven composite beams Bi 1+1 results from co-phasing and summing all neighbouring original beams B £ and B i+1 (i = 1 to 7) . Co- phasing was achieved by phase shifting the phase φ A of the first one of two neighbouring beams Bi by Δφi = 0 and the phase φ i+1 of the second one of two neighbouring beams B i+1 by Δφi + i = -7π/8 for all pairs of neighbouring beams. The composite beams have not been scaled, therefore they appear in the figure with a lower amplitude than the original beams . In figure 6b, in addition to the phase shifts of Δφi = 0 and Δφi + i = - n/ 8 , the amplitude of the respective first neighbouring beam Bi was multiplied by 0.8 and the amplitude of the respective second neighbouring beam B i+1 by 1.2 before summing. As a result, the generated composite beams B ± i+1 in figure 6b are shifted somewhat to the left as compared to the composite beams in figure 6a. By varying the factors with which the amplitudes of the original beams are multiplied, the composite beams can thus be positioned at any angle between two original beams . This approach enables in addition that several beams can be formed between every two neighbouring original beams simply by applying different sets of factors for the multiplication of the amplitudes of the original beams, which leads to an arbitrarily fine angular resolution. Finally, figures 7a and 7b show the power distribution over different non-orthogonal beams used in a base station by means for estimation of the direction of arrival of uplink signals. Both distributions correspond to the case that the signals from the terminal reach the receive antenna array of the base station perpendicularly, which is here to correspond to an azimuth angle of 0°. In figure 7a, the direction of arrival is to be estimated from the power distribution over 8 beams, all being formed by a first digital phasing network. The relation between the different beams and the different angles of arrival are the same as e.g. in figure 2d. In figure 7b, in contrast, the direction of arrival is to be estimated from the power distribution over 15 beams, including 7 composite beams formed in between the 8 original beams according to the invention. As can be seen in figure 7a, beams number 4 and number 5 have the maximum power. Accordingly, the means for estimating the direction of arrival are not able to determine the best direction for the downlink beam but only a best area which is lying between the angles of beam number 4 and beam number 5. In figure 7b, the maximum power belongs clearly to beam number 8, positioned exactly between original beams 4 (here beam 7) and original beam 5 (here beam 9) and therefore at an angle of 0°. This shows that in the latter case, the best direction for the downlink beam can be determined much more accurately.

Claims: C l a i s Base station for a radio communications network, comprising: a first phasing network (31) for forming beams (B 1 -B 4 ) for fixed reception angles out of signals provided by a receive antenna array and for outputting the signals constituting said beams (B 1 -B 4 ) ; a second phasing network (33) for co-phasing and summing the signals provided by the first phasing network for at least two neighbouring beams (B 2/ B 3 ), thus forming a beam (B 23 ) for a reception angle in- between the at least two neighbouring beams (B 2 ,B 3 ), and for scaling amplitude and/or power of each resulting beam (B 23 ) with a predetermined factor; and means for estimating the direction of arrival in the uplink from the beams (B 1 -B 4 , B 23 ) provided by the first and the second phasing network (31,33) . Base station according to claim 1, further comprising a receive antenna array for receiving signals from a terminal and for providing the received signals to the first phasing network (31) of the base station and a transmit antenna array for transmitting a beam in the estimated direction of arrival . 3. Base station according to claim 1 or 2 , wherein the first phasing network (31) is designed to form orthogonal fixed reception beams. 4. Base station according to claim 1 or 2 , wherein the first phasing network is designed to form non-orthogonal fixed reception beams. 5. Base station according to one of claims 1 to 4, wherein the first phasing network (31) is designed to form four beams (Bi-B out of the signals received from four receive antennas . 6. Base station according to one of claims 1 to 4, wherein the first phasing network is designed to form eight beams (B- L -Bg) out of the signals received from eight receive antennas . 7. Base station according to one of the preceding claims, wherein the second phasing network (33) is suited for scaling amplitude and/or power of the beams (B 23 ) formed in between two neighbouring beams (B 2 ,B 3 ) according to the amplitude and/or power of the beams (B x -B 4 ) formed by the first phasing network (31) in a way that the gain of all formed beams (B 1 -B 4/ B 2 _ 3 ) is equal. 8. Base station according to one of the preceding claims, wherein the second phasing network (33) is suited for scaling amplitude and/or power of the beams (B 23 ) formed in between two neighbouring beams (B 2 ,B 3 ) according to the amplitude and/or power of the beams (B 1 -B 4 ) formed by the first phasing network (31) in a way that the signal- to-noise ratio for each formed beam (B 1 -B 4< B 23 ) is equal in case that the same signal is arriving to each beam (B 1 -B 4( B 2 _ 3 ) . 9. Base station according to one of the preceding claims, wherein the second phasing network (33) is suited for scaling amplitude and/or power of the beams (B 2 _ 3 ) formed in between two neighbouring beams (B 2 ,B 3 ) according to the amplitude and/or power of the beams (Bi-B 4 ) formed by the first phasing network (31) in a way that the signal- to-interference-and-noise ratio for each formed beam (B 1 -B 4/ B 23 ) is equal in case that the same signal is arriving to each beam (B x -B 4/ B 2 _ 3 ) . 10. Base station according to one of the preceding claims, wherein the second phasing network is suited for co- phasing and summing the signals of all neighbouring beams (B x -B 4 ) formed by the first phasing network. 11. Base station according to one of the preceding claims, wherein the second phasing network is suited for multiplying the signals provided by the first phasing network for two neighbouring beams (Bi,B i+1 ) in between which a composite beam (Bi_ i+1 ) is to be formed with at least one pair of different predetermined factors before co-phasing and summing in order to obtain at least one beam in-between the two neighbouring beams at at least one predetermined azimuth angle. 12. Base station according to one of the preceding claims, wherein the means for estimating the direction of arrival in the uplink are suited to evaluate the power of the beams provided by the first and the second phasing network for estimating the direction of arrival . 13. Base station according to one of the preceding claims, wherein the first and the second phasing networks are analogue phasing networks. 14. Base station according to one of the preceding claims, wherein the first and the second phasing networks (31,33) are digital phasing networks in which a complex valued weight vector represents each beam (B α -B 4 ) in the digital domain. 15. Base station according to claim 14, wherein in the first and the second digital phasing network (31,33) complex weights are stored that are to be applied to incoming signals for forming the respective beams. 16. Base station according to claim 14 or 15, wherein the second phasing network (33) is suited for co-phasing and summing at least two neighbouring beams (B 2 ,B 3 ) by rotating the phase angle of at least one of the vectors (b 17 b 2 ) representing one of the two neighbouring beams (B 2 ,B 3 ) for obtaining two vectors with the same phase angle and by summing said vectors (b 2 ,b 3 ) for obtaining a single vector (b 23 ) representing a beam (B 23 ) in between the two neighbouring beams (B 2 ,B 3 ) . 17. Base station according to one of the preceding claims, further comprising means for estimating the angular spreading of the received signals based on the beams formed by the first and the second phasing network. 18. Base station module for a base station comprising a phasing network (33) according to the second phasing network of one of the preceding claims . 19. Method for enhancing the angular resolution in the estimation of the direction of arrival of signals in the uplink in a base station of a radio communications network, comprising: receiving uplink signals with a receive antenna array of the base station; forming first beams (B 1 -B 4 ) for fixed angles of arrival out of the received signals in a first phasing network (31) and outputting the signals constituting said beams (B- L -B ; forming at least one composite beam (B 23 ) in-between at least two neighbouring ones of the first beams (B 2 ,B 3 ) in a second phasing network (33) by co-phasing and summing the signals belonging to the neighbouring beams (B 2 ,B 3 ) and by scaling amplitude and/or power of each resulting composite beam with a predetermined factor; and estimating the direction of arrival of the received signals based on the first beams (B 1 -B 4 ) and the composite beams (B 23 ) . 20. Method according to claim 19, further comprising forming and outputting a downlink beam in the estimated direction of arrival of the uplink signals . 21. Method according to one of claims 19 to 20, wherein amplitude and/or power of the beams (B 2 _ 3 ) formed in between two neighbouring beams (B 2 ,B 3 ) are scaled according to the amplitude and/or power of the beams formed by the first phasing network. 22. Method according to one of claims 19 to 21, wherein the factor for scaling is set to a value leading to an equal gain for each formed beam (B 1 -B 4 ,B 23 ) . 23. Method according to claim 22, wherein the factor for scaling is set to a value which compensates the loss of 0.67 dB for all beams (B 23 ) formed exactly in the middle of two neighbouring first beams (B 2 ,B 3 ) in case of a receive antenna array with four antennas and orthogonal first beams. 24. Method according to claim 22, wherein the factor for scaling is set to a value which compensates the loss of 0.86 dB for all beams formed exactly in the middle of two neighbouring beams in case of a receive antenna array with eight antennas and orthogonal first beams. 25. Method according to one of claims 19 to 21, wherein the factor for scaling is set to a value leading to an equal signal-to-noise ratio (SNR) for each formed beam. 26. Method according to one of claims 19 to 21, wherein the factor for scaling is set to a value leading to an equal signal-to-interference-and-noise ratio (SINR) for each formed beam. 27. Method according to one of claims 19 to 26, wherein the second phasing network forms composite beams (B n ,B n ,B 34 ) in between each of the neighbouring first beams (B^B^ formed by the first phasing network. 28. Method according to one of claims 19 to 27, further comprising multiplying the signals provided by the first phasing network for two neighbouring beams (Bi,B i+1 ) in between which a composite beam (Bi i+1 ) is to be formed with a different predetermined factor before co-phasing and summing in order to obtain a beam in-between the two neighbouring beams at a predetermined azimuth angle. 29. Method according to one of claims 19 to 27, further comprising multiplying the signals provided by the first phasing network for two neighbouring beams with different pairs of predetermined factors in order to obtain differently weighted pairs of signals for each of the neighbouring beams, and subsequently co-phasing and summing each pair of signals in order to obtain a plurality of beams in between the two neighbouring beams at predetermined azimuth angles. 30. Method according to one of claims 19 to 29, wherein the beams are formed by analogue first and second phasing networks . 31. Method according to one of claims 19 to 29, wherein the beams are formed by digital first and second phasing networks (31,33) in which a complex valued weight vector represents each beams in the digital domain. 32. Method according to claim 31, wherein the first beams are formed by applying complex weights to the received signals in the first digital phasing network (31) , and wherein the co-phasing and summing of the signals of neighbouring beams is carried out in the second digital phasing network (33) by applying to said signals of the formed beams for each to be formed composite beam further complex weights causing a phase angle rotation at least of one of the vectors (b 2 ,b 3 ) representing the two neighbouring beams (B 2 ,B 3 ) for obtaining two vectors with the same phase angle and by summing said vectors (b 2 ,b 3 ) . 33. Method according to claim 32, wherein the co-phasing is carried out by rotating the phase angles of the vectors (b 2 ,b 3 ) of two neighbouring beams (B 2 ,B 3 ) by 0 and |3π/4| respectively in case of a receive antenna array with four antennas and orthogonal first beams. 34. Method according to claim 32, wherein the co-phasing is carried out by rotating the phase angles of the vectors of two neighbouring beams by 0 and |7π/8| respectively in case of a receive antenna array with eight antennas and orthogonal first beams. 35. Method according to one of claims 19 to 34, further comprising estimating the angular spreading of the received signals base on the formed first and composite beams .

Inventors: YLITALO JUHA, YLITALO, JUHA
Applicants: NOKIA CORP, YLITALO JUHA, NOKIA CORPORATION, YLITALO, JUHA
Application year: 2000
Main classification: H01Q1
IPC codes: G01S3, H01Q1, H01Q21, H04B7