METHOD AND DEVICE FOR SEPARATING A MIXTURE OF SOURCE SIGNALS

Abstract: Device and method for separating a mixture of source signals to regain the source signals, the device and method being based on measured signals, the invention comprises: bringing each measured signal to a separation structure including an adaptive filter, the adaptive filter comprising filter coefficients; using a generalised criterion function for obtaining the filter coefficients, the generalised criterion function comprising cross correlation functions and a weighting matrix, the cross correlation functions being dependent on the filter coefficients; estimating the filter coefficients, the resulting estimates of the filter coefficients corresponding to a minimum value of the generalised criterion function; and updating the adaptive filter with the filter coefficients.

Description: Method and device for separating a mixture of source signals TECHNICAL FIELD The present inventions relates to a metod and device for separating a mixture of source signals to regain the source signals. BACKGROUND OF THE INVENTION In recent time several papers concerning signal separation of dynamically mixed source signals have been put forward [1-3, 8, 17, 19, 20]. In principle it is possible to separate the sources exploiting only second order statistics, cf. [8]. The blind signal separation problem with dynamic/convolutive mixtures is solved in the frequency domain in several papers presented, cf. [3, 20]. Basically, dynamic source separation in the frequency domain aims to solve a number of static/instantaneous source separation problems, one for each frequency bin in question. In order to obtain the dynamic channel system (mixing matrix), the estimates corresponding to different frequencies bins, have to be interpolated. This procedure seems to be a nontrivial task, due to scaling and permutation indeterminacies [16]. The approach in the present paper is a "time-domain approach", see [8], which models the elements of the channel system with Finite Impulse Response (FIR) filters, thus avoiding this indeterminacies. A quasi-maximum likelihood method for signal separation by second order statistics is presented by Pham and Garat in [1 1]. An algorithm is presented for static mixtures, i.e. mixing matrices without delays. Each separated signal s, i=l ,...,M is filtered with a Linear Time Invariant (LTI) filter h_. The criterion used is the estimated cross-correlations for these filtered signals. The optimal choice of the filter h„ according to [1 1], is the filter with frequency response inversely proportional to the spectral density of the corresponding source signal. The filters .,, i=l,..., M are thus whitening filters. However, the spectral densities of the source signals are usually unknown, and perhaps time varying. One approach is to estimate these filters as done in the present paper and in the prediction error method as presented in [1]. Moreover, several aspects of the algorithm presented in [8] remained open. THE MOST CHARACTERIZING FEATURES OF THE INVENTION Characteπzing features of the present invention, 1 e the method for separating a mixture of source signals to regain the source signals, are bπnging each measured signal to a separation structure including an adaptive filter, the adaptive filter comprising filter coefficients; using a generalised cπteπon function for obtaining the filter coefficients, the generalised cπteπon function comprising cross correlation functions and a weighting matrix, the cross correlation functions being dependent on the filter coefficients, estimating the filter coefficients, the result' ing estimates of the filter coefficients corresponding to a minimum value of the generalised cπteπon function; and updating the adaptive filter with the filter coefficients Other characteπzing features of the present invention, 1 e the device for separating a mixture of source signals to regain the source signals, the input to the device being based on measured signals, the device compπses. signaling links for bnnging each measured signal to a separation structure including an adaptive filter, the adaptive filter compπsing filter coefficients, a generalised cπteπon function means for obtaining the filter coefficients, the generalised cπteπon function means compπsing cross correlation functions and a weighting matrix, the cross correlation functions being dependent on the filter coefficients, means for estimating the filter coefficients, the resulting estimates of the filter coefficients corresponding to a minimum value output of the generalised cπteπon function, and updating means for updating the adaptive filter with the filter coefficients Specific fields of application of the present invention include mobile telephone technology, data communication, heaπng aids and medical measuπng equipment, such as ECG Also included is echo cancelling which can pπmaπly occur in the telecommunications field BRIEF DESCRIPTION OF THE DRAWINGS Figure 1 shows the empiπcal and true parameter vaπances of a preferred embodiement of the present invention compared to a pπor art signal separation algoπthm Figure 2 shows the estimated mean value as a function of relative frequency of a preferred embodiement of the present invention compared to a pπor art signal separation algonthm Figure 3, shows the parameter vaπances as a function of relative frequency of a preferred embodiement of the present invention compared to a pπor art signal separation algoπthm DESCRIPTION OF PREFERRED EMBODIMENTS In the present invention a signal separation algoπthm is deπved and presented. A main result of the analys is an optimal weighting matπx. The weighting matπx is used to device a practical algoπthm for signal separation of dynamically mixed sources. The deπved algoπthm significantly improves the parameter estimates in cases where the sources have similar color In addition the statistical analysis can be used to reveal attainable (asymptotic) parameter vaπance given a number of known parameters The basis for the source signals, m the present paper, are M mutually uncorrelated white sequences These white sequences are termed source generating signals and denoted by £ (n) where k=l ,..., M. The source generating signals are convolved with linear time-mvaπant filters G k (q)/F k (q) and the outputs are, χ{n) = [x l _n) i f W = = K Λ ((q< )ξ(n) ξι (π) , (GM) G M (q) referred to as the source signals and where q and T is the time shift operator and matnx transpose, respectively. The following assumptions are introduced A 1 The generating signal £(n) is a realization of a stationary, white zero-mean Gaussian process; ξ(n) e N(0, Σ), ∑ = dιag(σ, 2 , , σ 2 ) A2 The elements of K(q) are filters which are asymptotically stable and have minimum phase Condition Al is somewhat restπctive because of the Gaussian assumption However, it appears to be very difficult to evaluate some of the involved statistical expectations unless the Gaussian assumption is invoked. The source signals x(n) are unmeasurable and inputs to a system, referred to as the channel system. The channel system produces M outputs collected in a vector y( n) ymj JM nJ y, ( πj B(q)x(n) which are measurable and referred to as the observables. In the present paper the channel system, B(q), given in 1 β 12 (q) 5ι w (q) _B(q) = ^21 (q) ■ β(,v/- i)Λ/ (q) 5 v/l (q) 5. /(.v/- i ) (q) l where B 1J (q), ι,j=l,.. ,M are FIR filters The objective is to extract the source signals from the observables. The extraction can be accomplished by means of an adaptive separation structure, cf [8]. The inputs to the separation structure are the observable signals The output from the separation structure, s,(n),. .,s M (n), depend on the adaptive filters, D y (q, θ), I, j = 1 , , M, and can be wπtten as a(n, θ) — [b \ ( n s {n, θ)] ' = D(q, θ)y(n) where θ is a parameter vector containing the filter coefficients of the adaptive filters That is the parameter vector is θ=[d n τ d MM ~] T w nere d ψ ι,j=l , ,M are vectors containing the coefficients ofD, j (q, θ), ι, j = 1, ., M, respectively Note, that unlike B(q) the separation matπx D(q, θ) does not contain a fixed diagonal, cf [6, 13] Most of the expressions and calculations m the present paper will be deπved for the two-input two-output (TITO) case, M=2 The mam reason for using the TITO case is that it has been shown to be parameter identifiable under a set of conditions, cf [8] However, the analysis in the cuπent paper is applicable on the more general multiple-input multiple-output (MIMO) case, assuming that problem to be parameter identifiable as well Assuming that N samples of y,(n) and y 2 (n) are available, the cπteπon function proposed in [8], reads as V(θ) = ∑ . -,(*;*), k=-U where To emphasize the dependence on θ equation (2.6) can be rewπtten as - d (i)R, Jiy ,(k + ,) + ^^d 13 (»)d 21 (/)Λ ysϊl (λ- - . + . where the notation d 12 (i) denotes the rth coefficient of the filter D ]2 (q). For notational simplicity, introduce the following vector as τχ(θ)=[R, ιa:t (-U_θ) R„„(U,Θ)] T where the subscπpt N indicates that the estimated cross-covaπances are based on N samples Fuπhermore, introduce a positive definite weighting matrix (θ) which possibly depends on θ too. Thus, the cπteπon, in equation (2.6), can be generalized as which will be investigated. Note, the studied estimator is closely related to the type of non-linear regressions studied in [15] The estimate of the parameters of interest are obtained as θv = argmin V,v(0) θ Although the signal separation based on the cπteπon (2.6) has been demonstrated to perform well in practice, see for example [12], there are a couple of open problems in the contribution [8] : 1. It would be interesting to find the asymptotic distribution of the estimate of Θ N . Especially, an expression for the asymptotic covariance matrix is of interest. One reason for this interest, is that the user can investigate the performance for various mixing structures, without performing simulations. Potentially, further insight could be gained into what kind of mixtures that are difficult to separate. The asymptotic covariance matrix would also allow the user to compare the performance with the Cramer-Rao Lower bound (CRB), primarily to investigate how far from the optimal performance of the prediction eπor method the investigated method is. An investigation of the CRB for the MIMO scenario can be found in [14]. 2. How should the weighting matrix W(θ) be chosen for the best possible (asymptotic) accuracy? Given the best possible weighting, and the asymptotic distribution, one can further investigate in which scenarios it is worthwhile applying a weighting W(θ) ≠ I, where I denotes the identity matrix. The purpose of the present contribution is to • Find the asymptotic distribution of the estimate of Θ N . • Find the weighting matπx W(θ) that optimizes the asymptotic accuracy. • Study an implementation of the optimal weighting scheme. In addition to Al and A2 the following assumptions are considered to hold throughout the description: A3. Assume that the conditions C3-C6 in [8] are fulfilled, so that the the studied TITO system is parameter identifiable. A4. The (minimal) value of U is defined as in Proposition 5 in [8]. A5. ||θ|| < ∞, i.e. θ 0 is an interior point of a compact set D M . Here, θ 0 contains the true parameters. This section deals with the statistical analysis and it will begin with consistency. The asymptotic properties (as N -∞ ) of the estimate of Θ (θ Λ )ιs established in the following However, first some preliminary observations are made In [8] it was shown that 1 As _V → oo, R, .(k,θ) -r R, ,.(k,θ) with probability one (w p 1) Thus Vv(θ) -r V{θ), pl where V(θ) = -τ r (θ)W(θ)τ(θ), τ(θ) = [R. x _,(-V,θ) „„(£ /• , β)] : The convergence in (31) is uniform m a set D M , where θ is a member hm ..up \\V f .(θ) V( β )|| = 0 pi Furthermore, since the applied separation structure is of finite impulse response (FIR) type, the a gr'adient is bounded dVv(θ) max < sup <C wpl, _<ι<π0 [g _> dθ_ for larger than some N 0 < ∞ In equation (34), C is some constant, C < ∞, and nθ denotes the dimension of θ The above discussion, together with the identifiability analysis [8] then shows the following result Result 1 - Λ → co θ ->• θo wpl Having established (strong) consistency, the asymptotic distπbution of θ is considered Since the θ\ minimizes the cπteπon VJΘ) V..(θ\) = 0 where V s denotes the gradient of \ N Bvthe mean value theorem. 0= J. β ) = lv(0o)-K'.ø ξ )(0 γ -0o) where θ is on a line between θ and θ 0 Note, since Θ Λ is consistent, the θ - θ 0 and consequently, θ ξ - θ 0 , as N - Next, investigate the gradient evaluated at θ 0 (for notational simplicity, let W(Θ)=W) Vl / (θ 0 ) = G T Wr N (θ 0 )-- ϊ G Wτ (θ 0 ) where dry(g) G = dθ I 9-β. Note, evaluation of G is straightforward, see for example [8] The introduced approximation does not affect the asymptotics, since the approximation error goes to zero at a faster rate than does the estimate of r N (θ 0 ) Furthermore, since r N (θ 0 ) = 0, the asymptotic distnbution of V N (Θ) is identical to the asymptotic distπbution of G τ Wr Λ N (θ 0 ), where dr(θ) I G = dθ I θ=9 0 Applying for example Lemma B 3 in [15], and using the fact that both s (n θ 0 ) and s-,(n,θ 0 ) are stationary ARMA processes one can snow tha t (v / N)G τ Wr Λ (θ 0 ) converges in distπbution to a Gaussian random vector, 1 e ,\ G τ Wr (θ 0 ) £ 4Λ (0 G T WMWG) where XI = im Λ E'τv(θ Q )τ',(θ 0 ) This means that the gradient vector, is asymptotically normally distπbuted, with zero-mean and with a covaπance matπx M Before presenting the mam result of the current paper, the convergence of the Hessian matπx V" must be investigated. Assuming that the limit exists, define V u [θ) = hm V/', {θ). V-+00 To establish the convergence of V" v (θ^), the following (standard) inequality is applied li tf (e<) - , where || || F denotes the Frobenius norm. Due to the FIR separation structure, the second order deπvatives are continuous. Moreover, since Θ E converges w.p.l to θ 0 , the first term converges to zero w.p. l . The second term converges also to zero w.p. l . This can be shown using a similar methodology that was used to show (3 3) Note also that since the third order deπvatives are bounded, the convergence is uniform in θ. It is, now, straightforward to see that the limiting Hessian V-" can be wπtten as V " {θ 0 ) = hm V"{ Θ 0 ) = G T WG v, p 1 /V→oo Thus, for large N, J_V(6» jV - θ_) ~ χ/N( G τ WG)- l G τ Wτ N (θ 0 ) , assuming the inverses exists (geneπcally guaranteed by the identifiability conditions in A3 Here all approximation eπors that goes to zero faster than 0( have been neglected Finally, the following result can be stated Consider the signal separation method based on second order statistics, where Θ Λ N is obtained from (2.10). Then the normalized estimation error, v / (N)(θ Λ N -Θ N ), has a limiting zero-mean Gaussian distribution SN(Θ V -θ_) &ΛsM( Q ,P), where P- (G T WG)- l G T WMWG{G T WG)- 1 Obviously, the matπx M plays a central role, and it is of interest to find a more explicit expression For simplicity we consider only the case when the generating signals are zero-mean, Gaussian and white (as stated in Assumption Al). It seems to be difficult to find explicit expressions for the non-Gaussian case. Note also that this is really the place where the normality assumption in A 1 is crucial. For example, the asymptotic normality of J(Nr Λ N (θ 0 ) holds under weaker assumptions Theorem 641 in [5] indicates precisely how the components of M can be computed These elements are actually rather easy to compute, as the following will demonstrate Let β τ= ∑ R. l ,Λp.θo)R,„ i {p + τ,θo Furthermore, introduce the following Z-transforms ΦJ-) = ∑ R,,__(k θ 0 ):- Φ 2 (--)= ∑ R„„(k_θ 0 )r Then it follows that Thus, the β τ 's are the covaπances of an ARMA process with power spectrum _(z ~l )Φ ) = Computation of ARMA covaπances is a standard topic, and simple and efficient algoπthms for doing this exists, see for example [ 15, Complement C7 7] Given β t forτ=0, ,2U, the weighting matπx can, hence, be constructed as W - βl β β β_υ β β. Thus, in the present problem formulation the separated signals are distorted with the determinant of the channel system the channel system determinant equals det{B(z)}, and one may define the reconstructed signals as ■ 5, n , tf det {_D(q θ) } as long as det{D(q, θ 0 )} is minimum phase To complete our discussion, it is also pointed out how the matπx G can be computed The elements of G are all obtained in the following manner sing Equation (2 8) it follows that ' d . -, (l ) R j . y k - t - i øfl,„,(*. fl) which are straightforward to compute Next, consider the problem of choosing Our findings are collected in the following result The asymptotic accuracy of Θ Λ , obtained as the minimizing argument of the cπteπon (2 10), is optimized if W = W 0 = M ' For this choice of weighting, P(W 0 ) = (G T M 'G) The accuracy is optimized in the sense that P(W 0 ) - P(W) is positive semi-definite for all positive definite weighting matπces W The proof follows from well-known matπx optimization results, see for example [9, Appendix 2] The result could have been deπved directly from the ABC theory in [15, Complement C4.4] However, the result above itself is a useful result, motivating the presented analysis. Before consideπng the actual implementation of the optimal weighting strategy, let us make a note on the selection of U This parameter is a user-defined quantity, and it would be interesting to gam some insight into how it should be chosen. Note, Assumption A3 states a lower bound for U with respect to identifiability. The following result may be useful Assume that the optimal weighting W 0 is applied m the cπteπon (2 10) Let P L ( ) denote the asymptotic covaπance for this case Then P L ( 0 ) > P L .,(W 0 ) The proof follows immediately from the calculations m [ 15 , Complement C4 4] Note that, when the optimal weighting. W 0 is applied the matπces {P L ( " W 0 )} forms a non-mcreasmg sequence However, in practice one must be aware that a too large value of U in fact may deteπorate the performance This phenomenon may be explained by that a large value of U means that a larger value of N is required in order for the asymptotic results to be valid In the present section a compaπson of signal separation based on an algoπthm within the scope of the present invention and the algoπthm in [8] will be made. The purpose for the compaπson is to show the contπbution of the present invention. Put differently, does the weighting lead to a significant decrease of the parameter vaπance? In all of our simulations, U=6. Furthermore, the term relative frequency is used in several figures. Here relative frequency corresponds to f r = 2F/F S where F s is the sampling rate, e.g. f re) = 1 is equal to π. Here the channel system is defined by B ]2 (q)=0.3+0.1q ' andB 21 (q)=0 l+0.7q '. The source signal x,(n) is an AR(2) process with poles at radius 0.8 and angles π/4. The second source signal is, also, an AR(2) process. However, the poles are moved by adjusting the angles in the interval [0,π/2], while keeping the radius constant at 0 8. At each angle 200 realizations have been generated and processed by the channel system and separation structure. That is to say, for each angle the resulting parameter estimates have been averaged. Finally, each realization consists of 4000 samples In figure 1 the empincal and true parameter vaπances are depicted First, note the good agreement between the empincal and theoretical vaπances. Second, observe that the proposed weighting strategy for most angles give πse to a significant vaπance reduction In figure 1, the parameter vaπances as a function of relative frequency " *" empincal vaπance of the pnor art signal separation algorithm, " +" empincal vaπance o f the proposed weighting strategy The solid line is the true asymptotic vaπance of the unweighted algoπthm, and the dashed line is the true asymptotic vaπance for the optimally weighted algoπthm The dotted line is the CRB Apparently, it gets more difficult to estimate the channel parameters when the source colors are similar. Therefore, in figures 2 and 3 a more careful examination of the parameter accuracy is presented. The angles of the poles are m the interval [40°, 50°] In figure 2, the estimated mean value as a function of relative frequency " *" empincal mean value of the pπor art signal separation algoπthm, -r" empincal mean value of the proposed weighting strategy The solid lines correspond to the true parameter values Note that the optimally weighted algoπthm gets biased, although less biased than a pπor art signal separation algoπthm This bias is probably an effect of the fact that the channel estimates of the unweighted algoπthm are rather inaccurate, making the weighting matπx inaccurate as well In tigure 3, the parameter variances is depicted as a function of relative frequency, ' *" empmca! vaπance of the prior art signal separation algorithm [8]; ' ' +" empirical variance of the proposed weighting strategy. The solid line is the true asymptotic variance of the unweighted algorithm, and the dashed line is the true asymptotic variance for the optimally weighted algorithm. The dotted line is the CRB. As is indicated by the figures 1-3, the present invention increases the quality of the signal separation. Further details of the present invention are that the method, according the device for separating signals, is repeatedly performed on the measured signal or on fractions thereof. Also, the method may be repeatedly performed according to a predetermined updating frequency. It should be noted that the predetermined updating frequency may not be constant. Further, the number of filter coefficents is predetermined. Finally, the number of filter coefficents is arranged to be predetermined in the above embodiment. REFERENCES [1] H. Broman, U. Lindgren, H. Sahlin, and P Stoica. "Source Separation. A TITO System Identification Approach", esp, 1994 [2] D.C.B. Chan. Blind Signal Separation, PhD Thesis, University of Cambπdge, 1997 [3] F. Ehlers and H.G. Schuster. Blind separation of convolutive mixtures and an application in automatic speech recognition in a noisy environment. IEEE Trans, on Signal Processing 45(10):2608-2612. 1997. [4] M. Feder, AN. Oppenheim, and E Wemstein. Maximum likelihood noise cancellation using the EM algoπthmHEEE Trans, on Acoustics, Speech, and Signal Processing, ASSP-37:204-216 Feb. 1989. [5] W.A. Fuller. Introduction to Statistical Time Series John Wiley & Sons, Inc New York, 1996. [6] U Lindgren, H. Sahlm and H. Broman. Multi input multi output blind signal separation using second order statistics Technical Report CTH-TΕ-54, Department of Applied Electronics, 1996 [7] U. Lindgren and H. Broman. "Monitoπng the mutual Independence of the Output of Source Separation Algoπthms". In IEEE International Symposium on Information Theory and Its Applications, Victoπa B C, Canada, 1996 [8] U- Lindgren and H. Broman "Source Separation: Using a Cnteπon Based on Second Order Statistics". IEEE Trans on Signal Processing, SP-46(7), July, 1998 [9] L. Ljung. System Identification Theory for the User, Prentice-Hall. Εnglewood Cliffs, N J , 1987 [10] L. Ljung. Personal Communication, 1998 [ 1 1 ] D Tuan Pham and P Garat "Blind Separation of Mixture of Independent Sources Through a Quasi-maximum Likelihood Approach" IEEE Trans on Signal Processing, SP-45 1712-1725, July, 1997 [ 12] H Sahlm and H Broman "Separation of Real World Signals" Signal Processing, 64(1 ).103- 1 13, January, 1998 [ 13] H. Sahlin and H Broman A decorrelation approach to blind mimo signal separation In Proceedings ofICA, pages 383-388, 1999 [14] H. Sahlin and U. Lindgren "The Asymptotic Cramer-Rao Lower Bound for Blind Signal Separation". In the Procedings of the 8 th Signal Processing Workshop on Statistical Signal and Array Processing, pages 328-331, Corfu, Greece, 1996 [15] T. Sόderstrom and P. Stoica. System Identification. Prentice-Hall, London, U.K., 1989. [16] L. Tong, Y.R. Liu, V Soon, and Y. Huang Indetermmancy and identifiability of blind identification. [17] S van Gerven and D van Compernolle Signal Separation by symmetπc adaptive decorrelation: stability, convergence and uniqueness IEEE Trans on Signal Processing, 43:1602-1612, 1995 [ 18] M. Niberg and A.L. Swindlehurst. "Analysis of the Combined Effects of Finite Samples and Model Errors on Array Processing Performance".7EEE Trans, on Signal Processing, SP-42.1 -12, Nov. 1994. [19] H. Wu and J. Pnncipe A unifying cπteπon for blind source separation and decoπelatiom simultaneous diagonalization of correlation matπces In Proc of NNSP97, pages 496-505, Amelia Island. FL, 1997 [20] H. Wu and J. Pnncipe Simultaneous diagonalization in the frequency domain (sdif) for source separation. In ICA, pages 245-250, Aussois, France, 1999

Claims: PATENT CLAIMS 1 Method for separating a mixture of source signals to regain the source signals, the method being based on measured signals, the method compπses -bπngmg each measured signal to a separation structure including an adaptive filter, the adaptive filter compnsmg filter coefficients, -using a generalised cntenon function for obtaining the filter coefficients, the generalised cntenon function compnsmg cross coπelation functions and a weighting matnx, the cross correlation functions being dependent on the filter coefficients, -estimating the filter coefficients, the resulting estimates of the filter coefficients corresponding to a minimum value of the generalised cntenon function, and -updating the adaptive filter with the filter coefficients 2 Method according claim 1 , characterized in, that the weigthing matπx is dependent on the filter coefficients 3 Method according to claim 1 , characterized in, that the method is repeatedly performed on the measured signal or on fractions thereof 4 Method according to claim 3, characterized in, that the method is repeatedly performed according to a predetermined updating frequency 5 Method according to claim 1, characterized in, that the number of filter coefficents is predetermined 6 Device for separating a mixture of source signals to regain the source signals, the input to the device being based on measured signals, the device compπses -signaling links for bπngmg each measured signal to a separation structure including an adaptive filter, the adaptive filter comprising filter coefficients; -a generalised criterion function means for obtaining the filter coefficients, the generalised criterion function means comprising cross correlation functions and a weighting matrix, the cross correlation functions being dependent on the filter coefficients; -means for estimating the filter coefficients, the resulting estimates of the filter coefficients coπesponding to a minimum value output of the generalised criterion function; and -updating means for updating the adaptive filter with the filter coefficients. 7. Device according claim 6, characterized in, that the weigthing matrix is dependent on the filter coefficients. 8. Device according to claim 6, characterized in, the device is arranged to separate the measured signals or fractions thereof repeatedly. 9. Device according to claim 8, characterized in, that the device is ananged to separate the measured signals or fractions thereof according to a predetermined updating frequency. 10. Device according to claim 6, characterized in, that the number of filter coefficents is arranged to be predetermined. AMENDED CLAIMS [received by the International Bureau on 19 July 2000 (190700), original claims 1 and 6 amended, remaining claims unchanged (3 pages)] PATENT CLAIMS 1 Method for separating a mixture of source signals to regain the source signals, the method being based on measured signals, the method compπses - bπngmg each measured signal to a separation structure including an adaptive filter, the adaptive filter comprising filter coefficients, - using a generalised cntenon function for obtaining the filter coefficients, the generalised cntenon function comprising cross correlation functions and a weighting matnx (W), the cross correlation functions being dependent on the filter coefficients, - said weighting matrix (W), being an inverse matπx of a matnx (M) compnsmg estimation av covaπant matπx for a signal (z(t)), - said signal (z(t)) having a spectrum being a product of estimated spectrum of a incoming source-signal and the determinant of an estimated transformation function of a mixing filter, - estimating the filter coefficients, the resulting estimates of the filter coefficients corresponding to a minimum value of the generalised cntenon function, and - updating the adaptive filter with the filter coefficients 2 Method according claim 1, characterized in, that said spectrum of the incoming source-signal is unknown and the weighting matrix (W) considers an assumed spectrum 3 Method according claim 1 or 2 characterized in, that the weighting matπx is dependent on the filter coefficients 4 Method according to claim 1, characterized in, that the method is repeatedly pertormed on the measured signal or on fractions thereof 5 Method according to claim 4, c aracterized in, that the method is repeatedly performed according to a predetermined updating frequency. 6. Method according to claim 1, characterized in, that the number of filter coefficients is predetermined. 7. Device for separating a mixture of source signals to regain the source signals, the input to the device being based on measured signals, the device comprises: - signalling links for bringing each measured signal to a separation structure including an adaptive filter, the adaptive filter comprising filter coefficients; - a generalised criterion function means for obtaining the filter coefficients, the generalised criterion function means comprising cross correlation functions and a weighting matrix (W), the cross correlation functions being dependent on the filter coefficients; - said weighting matrix (W), being an inverse matrix of a matrix (M) comprising estimation av covariant matrix for a signal (z(t)), - said signal (z(t)) having a spectrum being a product of estimated spectrum of a incoming source-signal and the determinant of an estimated transformation function of a mixing filter, - means for estimating the filter coefficients, the resulting estimates of the filter coefficients corresponding to a minimum value output of the generalised criterion function; and - updating means for updating the adaptive filter with the filter coefficients. 8. Device according claim 7, characterized in, that the weighting matrix is dependent on the filter coefficients. 9. Device according to claim 7, characterized in, the device is arranged to separate the measured signals or fractions thereof repeatedly. 10. Device according to claim 9, characterized in, that the device is ananged to separate the measured signals or fractions thereof according to a predetermined updating frequency. 11. Device according to claim 7, characterized in, that the number of filter coefficients is arranged to be predetermined.

Inventors: GUSTAFSSON TONY, GUSTAFSSON, TONY
Applicants: GUSTAFSSON TONY, GUSTAFSSON, TONY
Application year: 2000
Main classification: H03H21
IPC codes: G06F17, G06K9, H03H21