Orthogonal transformations for interference reduction in multicarrier systems

Abstract: In order to reduce interference with other users, a multicarrier transmitter subjects a block of data to an orthogonal transformation, which confers a degree of randomization. The matrix has n columns and m rows, with n<m, and n may be equal to the size of the subsequent IFFT. In a cellular system, the transmitter of a base station may use several different such matrices.

Description: The present invention relates to a transmitter and a method as well as to a transmitting system for the wireless transmission of informational data and particularly to a technique for interference cancellation in OFDM communication. One technique to minimize interference in wireless transmission, particularly in OFDM systems, is the so-called random orthogonal transform (ROT). The principles of ROT are described in the European patent application 98 104 287.2 of Sony Corporation which is only to be regarded to be prior art according to Article 54(3) EPC. In the context of a communication between a transmitter and a receiver, the concept of ROT refers to an orthogonal conversion, which is performed by multiplying a ROT matrix M transmitter that is different for each communication to signal series to be sent. The ROT matrix M transmitter is the matrix of a linear transformation using an orthogonal basis (general definition of the matrix orthogonality). The signal series to which the orthogonal conversion, i.e. the ROT, is performed is sent by using a predetermined channel. Next, on the receiving side, the signal series before the orthogonal conversion is restored by multiplying an inverse ROT matrix M receiver to the received signal series. The matrix M receiver is chosen such that it complies with the equation M receiver *M transmitter =I, I being the identity matrix. In case the matrix M transmitter is a square matrix, M receiver is then the inverse matrix of the ROT matrix M transmitter . The process at the receiver consisting in multiplying the received data with the inverse ROT matrix is called inverse random orthogonal transformation. The transmitter performs a random orthogonal transformation by multiplying the signal series with the orthogonal matrix M transmitter . The receiver performs an inverse random orthogonal transformation by multiplying the received signal with the orthogonal matrix M receiver , wherein M receiver *M transmitter =I and M transmitter is the matrix used at the transmitting side of the communication partner. By performing the inverse random orthogonal transformation, the receiver restores the signal series as it was before the random orthogonal transformation carried out by the transmitting side of the communication partner. On the other side, a signal series received from another transmitter , i.e. from a transmitter that is not the communication partner of the receiver, is not restored because in that case the matrixes representing the random orthogonal transformation and the inverse random orthogonal transformation are not set to comply with the equation M receiver *M transmitter =I. Another important feature of the ROT conversion is that the ROT matrix M transmitter is created randomly. This can for example be achieved by preparing N Walsh vectors W 1 ,...,W N and by multiplying random phase rotation components e jZ1 ,..., e jZN to the N Walsh vectors to obtain a random phase rotation. The ROT matrix is then generated by combining the random phase rotation. A ROT is thereby directed to the orthogonal transform, i.e. to the linear transformation using orthogonal basis, wherein the orthogonal basis is randomly generated. In the following, the basic technique of ROT according to the application EP 98 104 287.2 will be explained in detail with reference to figures 8 to 10. In Fig. 8, reference numerals 105A, 105B denote respectively portable telephone device. Reference numerals 106A and 106B denote base stations of a wireless transmission system. As shown in Fig. 8, the portable telephone device 105A uses a predetermined channel to be engaged in radio communication with the base station 106A in the cell 101A. At the same time, the same channel is used in the adjacent cell 101B so that the portable telephone device 105B is engaged in radio communication with the base station 106B. At that time, for example, in the portable telephone devices 105A and 105B both QPSK modulation (Quadrature Phase Shift Keying; Four Phase Transition Modulation) is used as a modulation method of the sent data. The signal series of the modulated sending signal are defined as x (A) 2 , modulated sending signal are defined as x (A) 1 , x (A) 2; x (A) 3 , ... ... x (A) k-1 , x (A) k , x (A) k+1 , ... ... and x (B) 1 , x (B) 2 , x (B) 3 , ... ... x (B) k-1 , x (B) k , x (B) k+1 , ... ... The portable telephone device 105A groups N (N is an integer which is 1 or more) sending signal series x (A) n (n=1, 2, 3, ... ...). The grouped sending signal series x (A) k , ... ... x (A) k+N-1 and a predetermined Nth normal orthogonal matrix M A are multiplied in order as shown in the following equation. As a consequence, an orthogonal conversation is added to the sending signal series x (A) n (n=1, 2, 3, ... ...) and a resulting sending signal series y (A) n (n=1, 2, 3, ... ...) are sent in order. On the other hand, at the base station 106A which is a receiving side, when a sending signal CA is received from the portable telephone device 105A of the communication partner, N received signal series y (A) n (n = 1, 2, 3, ... ...) are grouped, and the grouped received signal series y (A) k , ..... y (A) k+N-1 are successively multiplied with an inverse matrix M A -1 of the Nth normal orthogonal matrix M A used on the sending side as shown in the following equation. As a consequence, the signal series X (A) n (n=1, 2, 3, ... ...) is restored which is equal to the signal series x (A) n (n =1, 2, 3 , ... ...) before orthogonal conversion. In the similar manner, at the time of sending data, the portable telephone device 105B groups the N sending signal series x (B) n (n=1, 2, 3, ... ...). The grouped sending signal series x (B) k , ... ... x (B) k+N-1 and the predetermined Nth normal orthogonal matrix M B are multiplied in order for each group as shown in the following equation. As a consequence, the orthogonal conversion is added to the sending signal series x (B) n (n=1, 2, 3, ... ...), and the resulting sending signal series y (B) n (n=1, 2, 3, ... ...) are sent in order. For reference, the Nth normal orthogonal matrix M B which is used in the portable telephone device 105B and the Nth normal orthogonal matrix M A which is used in the portable telephone device 105A are matrixes which are completely different from each other. At the base station 106B which is a receiving side, when the sending signal CB from the portable telephone device 105B of the communication partner is received, the N received receiving signal series y (B) n (n=1, 2, 3, ... ...) are grouped, and the grounded y (B) k , ..... Y (B) k+N-1 and the inverse matrix M B -1 of the Nth normal orthogonal matrix M B used at a sending side are multiplied in order for each group as shown in the following equation. Consequently, the signal series X (B) n (n=1, 2, 3, ... ...), which is equal to the signal series x (B) n (n=1, 2, 3, ... ...) before the orthogonal conversion, is restored. By the way, at the base station 106A, only the sending signal CA sent by the portable telephone device 105A reaches, but the sending signal CB sent by the portable telephone device 105B also reaches depending on the situation. In that case, the sending signal CB from the portable telephone device 105B acts as an interference wave I. When the signal level of the sending signal CB is large as compared with the sending signal CA from the portable telephone device 105A, trouble is caused to communication with the portable telephone device 105A. In other words, as the base station 106A, it is not recognized that the signal is a sending signal from either of the portable telephone devices 105A or 105B so that it is feared that the sending signal CB form the portable telephone device 105B is received by mistake. In such a case, the base station 106A groups the N received signal series y (B) n (n=1, 2, 3, ......) received from the portable telephone device 105B so that the demodulation processing is performed by multiplying the inverse matrix M A -1 to the grouped signal series y (B) k , ..... y (B) k+N-1 as shown in the following equation as in the normal receiving processing. However, as seen from the equation (5), the receiving signal series y (B) n (n=1, 2, 3, ... ...) from the portable telephone device 105B is a result obtained from a multiplication of the orthogonal matrix M B which is different from the orthogonal matrix M A so that the diagonal reverse conversion is not obtained even when the inverse matrix M A -1 is multiplied with the result that the original signal series x (B) n (n = 1, 2, 3, ... ...) is not restored. In this case, the received signal series becomes a signal series which is the original signal series x (B) n (n=1, 2, 3, ...) orthogonally converted with another orthogonal matrix consisting of M A -1 M B , so that the signal becomes ostensibly a noise signal, and even when the signal series is QPSK demodulated, the sending data of the portable telephone device 105B is not restored. In this manner, in the case of the radio communication system to which the present invention is applied, the orthogonal matrix which is different for each communication at the sending side is multiplied with the signal series. On the receiving side, the received signal series is multiplied with the inverse matrix of the orthogonal matrix which is used on the sending side (namely, the communication partner of its own station) so that the original signal series before the orthogonal conversion is restored. As a consequence, even when the same channel is used in the other communication, the restoration of the sent signal series by the other communication is avoided in advance with the result that the leakage of the data sent in the other communication can be avoided in advance. For reference, there is described here that the leakage problem is avoided when the sending signal CB of the portable telephone device 105B is received by the base station 106A. For the same reason, the leakage problem can be also avoided even when the base station 106B receives the sending signal CA of the portable telephone device 105A. Here, the orthogonal conversion using the orthogonal matrix and the inverse conversion thereof will be explained by using the signal transition view. In the beginning, the sending signal series x (A) n (n = 1, 2, 3, ... ...) of the portable telephone device 105A is QPSK modulated so that the π/4, 3π/4, 5π/4 or 7π/4 phase states can be assumed. As a consequence as shown in Fig. 9A, on the complex surface (IQ surface), the phase state is present at a position where the phase state becomes π/4, 3π/4, 5π/4 or 7π/4. When such sending signal series x (A) n (n=1, 2, 3, ... ...) is multiplied to the Nth normal orthogonal matrix M A , the resulting signal series y (A) n (n = 1, 2, 3, ... ...) becomes a random state as shown in Fig. 9B. On the other hand, at the base station 105A which is a receiving side, this signal series y (A) n (n=1, 2, 3, ... ...) is received. As described above, when the inverse matrix M A -1 of the orthogonal matrix M A which is used on the sending side is multiplied with this signal series y (A) n (n =1, 2, 3, .....), the resulting signal series X (A) n (n =1, 2, 3, .....) becomes the same as the original signal series x (A) n (n=1, 2, 3, ... ...) as shown in Fig. 9C so that the resulting signal series is brought back to the position of the phase state comprising π/4, 3π/4, 5π/4 or 7π/4 on the complex surface. Consequently, when the signal series X (A) n (n=1, 2, 3, .....) is subjected to QPSK demodulation, the sending data from the portable telephone device 105A can be accurately restored. Furthermore, since the sending signal series x (B) n (n = 1, 2, 3, ... ...) of the portable telephone device 105B is also QPSK modulated, π/4, 3π/4, 5π/4 or 7π/4 phase state is assumed with the result that the phase is present on the position comprising π/4, 3π/4, 5π/4 or 7π/4 on the complex surface as shown in Fig. 10A. When such sending signal series x (B) n (n = 1, 2, 3, ... ...) is such that the phase state becomes random as shown in Fig. 10B. In the case where such signal series y (B) n (n =1, 2, 3, ... ...) is received with the base station 106A which is not the communication partner, the signal series y (B) n (n=1, 2, 3, ... ...) becomes an interference wave for the base station 106A. However, the base station 106A does not recognize that the signal series is either the sending signal from the communication partner or the interference wave, the demodulation processing is performed as in the normal receiving processing. However, even when the inverse matrix M A -1 of the orthogonal matrix M A is multiplied with this signal series y (B) n (n=1, 2, 3, ... ...), the inverse matrix M A -1 is not the inverse matrix of the orthogonal matrix M B which is used at the sending time. As shown in Fig. 10C, the phase state is not brought back to the original state so that the phase state becomes a random state. Consequently, even when the signal series shown in Fig. 10C is QPSK demodulated, the sending data from the portable telephone device 105B is not restored. Though the randomizing according to ROT provides for an minimization of interference effects by the randomizing procedure, the interference is not canceled totally as this the case e.g. in TDMA. furthermore, as in OFDM systems usually no training sequence or midamble is used, the distinction between a wanted and an unwanted signal generally is difficult. In their article "Performance Comparison of Direct-Spread and Multi-Carrier CDMA Systems" (Vehicular Technology Conference, 1998, VTC 98, IEEE, Ottawa (Canada), 18-21 May 1998 and New York, 18 May 1998, pp. 2042-2046, XP 010 288 173, ISBN: 0-7803-4320-4) the authors A. Jalali and A. Gutierrez compare the forward link performance of a direct-spread CDMA system with a spreading bandwidth of 3.6864 MHz with the forward link performance of a multi-carrier (MC) system consisting of three carriers, each having a spreading bandwidth of 1.2288 MHz. Aside from providing a description of a MC method, which is under consideration for the forward link of next generation CDMA Cellular/PCS systems, this paper summarizes performance comparison results of the two systems for a data rate of 9.6 kbps with the IMT-2000 vehicular and pedestrian channel models. The results indicate that the two systems have comparable performance for the above data rate and the IMT-2000 channel models. The article "A Generalized View on Multicarrier CDMA Mobile Radio Systems with Joint Detection (Part I)" (Frequenz, Schiele und Schon GmbH, Berlin, Germany, July 1997, vol. 51, no. 7, pp. 174 to 185, XP 735 799) by P. Jung, F. Berens, and J. Plechinger presents a generalized view on MC-CDMA concepts for mobile radio applications and a comprehensive introduction to CDMA and multiple-access interference (MAI). The authors explain why joint detection (JD) is a mandatory prerequisite for hybrid frequency- and time-divided CDMA, which is a viable basis for third generation mobile radio systems. In this connection, the benefits of MC-CDMA over other CDMA concepts are discussed in an illustrative manner, and a flexible MC-CDMA concept is introduced and explained in detail. Thereby, signal generation in MC-CDMA is described in a continuous-time and discrete-time form, thus revealing the close relationship between the herewith presented flexible MC-CDMA and the traditional JD-CDMA concept. The discrete-time transmission model, which results from the continuous-time representation, is introduced to facilitate digital signal processing. This transmission model takes coherent receiver antenna diversity (CRAD) explicitly into account. Furthermore, four viable JD technologies suitable for the discussed flexible MC-CDMA concept are presented. Their structure and mode of operation are explained in detail, and their uplink performance is studied under a variety of different transmission conditions. random orthogonal transformation by means of a multiplication of a vector comprising the data of one block with the matrix. The data originating from the step of random orthogonal transforming are then transmitted. Thereby the matrix operation uses a matrix comprising n orthogonal columns, n being the number of data samples comprised in one of set blocks, wherein the number of rows of said matrix is larger than the number of said columns of said matrix. According to the present invention furthermore a method for the generation of matrices to be used for the random orthogonal transformation of blocks of data in a wireless transmission chain is provided. Thereby a square matrix with orthogonal column vectors and orthogonal row vectors is provided. The square matrix is divided to great M matrices the number of rows of each of that matrices being equal to M*n, n being the number of columns of each of that matrices and M being an integer larger than one. Each of that M matrices is than allocated to a transmitter in a transmission chain. Further advantages, objects and features of the present invention will come clearer from the following description of preferred embodiments of the present invention taken in conjunction with the annexed drawings. Figure 1 shows an overall view of a transmission system according to the present invention, Figure 2 shows a matrix operation as it is known from EP 98 104 287.2 of Sony corporation, which is only prior art according to Article 54(3) EPC, Figure 3 shows a matrix operation for ROT according to the present invention, Figure 4 and Figure 5 show the generation and allocation of ROT-matrices to different base stations, Figure 6 shows different ROT-operations to explain the interference cancellation effect of the present invention, Figure 7 shows the result of the matrix-multiplication of orthogonal matrices, Figure 8 shows a system structural view explaining a principle being the base of the present invention, Figure 9a to 9c are signal transition views explaining an operation at the time of receiving a sending signal from the communication partner in a radio communication (transmission) system, to which the present invention can be applied, Figures 10a to 10c are signal transition views explaining an operation of the time of receiving an interference wave in the radio communication system according to Figure 8, Figure 11 shows a further embodiment of the present invention, according to which in line with the random orthogonal transform step a convolutional coding/decoding is effected, Figure 12 shows the use of a ROT matrix for a convolutional coding, Figures 13 and 14 show the generation of a ROT matrix reconstructed from a convolution coding matrix and the division of said ROT matrix into three parts, Figure 15 shows the convolutional coding/decoding process effected by the multiplication with a ROT matrix according to the present invention, Figure 16 shows the multiplication of a ROT matrix with the transpose of said ROT matrix, Figure 17 shows the multiplication of a ROT matrix with the transpose of a matrix orthogonal to said ROT matrix, Figure 18 shows the generation of an equivalent vector on the basis of a multiplication of an input symbol and a ROT matrix, which equivalent vector is used for a convolutional coding/decoding, Figure 19 shows a Trellis state matrix, Figure 20 shows schematically the calculation of path metrics, and Figure 21 shows an original Trellis state matrix. With reference to Figure 1 the general structure of a transmission system according to the present invention will now be explained. Voice data for example from a hand set 1 are passed through A/D converter 2 and then supplied to a voice codec 3. The output of the voice codec 3 is supplied to a channel encoder 5. Alternatively or additionally other data, such as video data from a camera 4 or data from a laptop computer 6 can be input to the channel encoder 5. The channel encoded data are passed through a interleaver 7 and then given to a modulator 8 effecting the symbol mapping. The modulated data are the given to a random orthogonal transform (ROT) circuit 9 outputting transformed data to an inverse fast Fourier transformation (IFFT) circuitry 10. The output data from the IFFT 10 D/A converted 11 and then wirelessly transmitted 13 once they are upconverted 12. At the receiving side the wirelessly transmitted data are downconverted 14 A/D converted 15, past through a fast Fourier transformation circuit 16. The output data from the FFT 16 are the processed by a inverse ROT process 17. The output data from the inverse ROT circuitry 17 is passed through a bit mapping circuitry 18, a deinterleaver 19 and then supplied to a channel decoder 20. The channel decoder 20 optionally outputs decoded data to a monitor 21 (in case of video data), to a laptop computer 22 or to a voice decoder 23, a D/A converter 24 and the hand set 25 in case of voice data. The object of the present invention particularly lies in the procedures as they are effected by the ROT circuit 9 and the inverse ROT circuit 17. Figure 2 once again shows a ROT-matrix operation according to EP 98 104 287.2. An input symbol vector 26 comprising n data samples and emerging from the modulator 8, e. g. is multiplied with a ROT matrix 27 having n orthogonal column vectors and n orthogonal row vectors. With other words the input symbol vector 26 is multiplied with a square matrix 27. Therefore the ROT-operation generates a symbol vector 28 after the ROT-operation, wherein the transformed symbol vector 28 comprises again n data samples which were passed through a IFFT circuitry 10. ROT therefore is a technique which randomizes information data symbol vectors before the IFFT and the OFDM modulation by an orthogonal matrix. This randomization is untied after FFT, OFDM-demodulation in the receiving side. Interference signals are randomized by another matrix. Therefore some interference is left randomized after untying in the receiving side. The random orthogonal transform is just randomizing interference. As no training sequence or mid-amble is used is used in OFDM, it is difficult to distinguish a wanted signal from an interference signal. Figure 3 shows the ROT matrix operation according to the present invention. After the modulation the symbols are divided into a size adapted for the IFFT. The symbols are then treated as a vector of a complex number which size is n. According to the present invention, the input symbol vector 26 is multiplied with a ROT matrix 29 having more rows than columns. Note: Generally, when the input data are represented as a row vector, the ROT matrix has more columns than rows, and when the input data are represented as a column vector, the ROT matrix has more rows than columns. Particularly, the number of rows can be m times the number of columns. Therefore the number of symbols is increased by the ROT matrix operation. The number of symbols input to the ROT matrix operation therefore is 1/m of the size of the IFFT(n). The n column vectors are still mutually orthogonal. However, as there are e.g. 3n row vectors and therefor more row vectors than column vectors, these row vectors are no longer mutually orthogonal. (There are only n orthogonal bases of n element vectors.) By the ROT-matrix operation according to the present invention, in case the input symbol vector 26 comprises n symbols, the symbol vector 28 after the ROT operation will contain more samples, e.g. 3n samples in case orthogonal column vectors and 3n row vectors generate the ROT matrix 29. It is to be noted, that there are still existing additional (M-n) orthogonal column vectors which are not part of the matrix. These orthogonal but "unwritten" vectors are used to randomize interference. It is to be noted that the present invention is not limited to binary codes, the values of the vectors can also take higher values, as e.g. 0,1; 1,0;0,0 or 1,1. Figure 4 and figure 5 show an example for the generation of the oblong matrices according to the present invention. At first square matrix 31 comprising 3N orthogonal column vectors and 3N orthogonal row vectors is created. Said square matrix 31 is then divided e.g. in three oblong matrices ROT1, ROT2, ROT3. The oblong matrices ROT1, ROT2, ROT3 (29, 29', 29'') therefore will still have orthogonal column vectors, however the row vectors can no longer be orthogonal. The m*n columns of the square matrix therefore are divided into m oblong matrices. The matrices ROT1, ROT2, ROT3 satisfy the equation as it is shown in figure 7. The m oblong matrices can then be respectively allocated to different base station/mobile station transmission systems. For example the matrix ROT1 can be allocated to a base station 1 and mobile stations belonging to the base station 1, the matrix ROT2 (29') can be allocated to a transmission system comprising a base station 2 and mobile stations belonging to said base station 2, and the oblong matrix ROT3 (29'') can be allocated to a transmission system comprising a base station 3 and mobile stations belonging to said base station 3. (see figure 5). As it comes clear particularly from figure 5 in combination with figure 7 if one of said matrices is used in a base station 1 and the other matrix is used in another base station (2 or 3), any interference contributions can be canceled due to the orthogonally between the different matrices 29, 29', 29''. As it comes clear from figure 6, in the receiver 30 the randomization can be easily restored by multiplication with a transpose matrix ROT T . The wanted signal is restored by multiplying with a transpose matrix of ROT1. The receiver 30 keeps this matrix ROT1 t . Any interference signal which is randomized for example by ROT2 will be canceled by the multiplication procedure with a transpose matrix of ROT1, as ROT2 is orthogonal to ROT1. It is to be noted that the components of the ROT matrices can also assume complex values. In actual environment, the channels are not ideal and synchronization between the cells is not complete. In these cases, according to the present invention the interference is not canceled totally, but at least the interference is reduced more efficient than in the case of a randomization procedure as known from EP 98 104 287.2. According to a further aspect of the present invention, a plurality of mutually orthogonal matrices is used in one base station. With other words, a plurality of mutually orthogonal matrices is allocated to the same base station. The frequency band of OFDM can the be divided by these orthogonal matrices. Therefore, according to this aspect of the present invention, a multiple access technique in OFDM is provided. In OFDM systems interference symbols can be randomized by different orthogonal matrices, which individually randomize modulated symbols as shown above. Interference can be canceled by using non-square matrices, which randomize symbols orthogonally to each other. Oblong matrices increase the number of symbols after randomizing. According to the above-shown embodiments the increased symbols are only used to keep orthogonality with interference signals. However, according to still another aspect of the present invention, the multiplication with a ROT matrix can also be used for convolutional coding/decoding. For example a Viterbi algorithm can be used solving the randomization. Therefore, according to this aspect of the present invention, convolutional coding and the ROT matrix technique using oblong matrices is combined. As it is shown in Figure 11 the original channel coding can therefore be replaced the ROT multiplication operation, which stills keeps orthogonality with the interference signals. As it is shown in Figure 11, on the transmission side the ROT multiplication unit 9' simultaneously effects the convolutional coding. On the reception side, the unit 17' for multiplicating the deinterleaved symbol with the transpose of the ROT matrix used in the unit 9', simultaneously effects a convolutional decoding operation, such as for example, a Viterbi decoding. After the voice coding in the codec 3 the bit stream on the transmission side is modulated (modulator 8') into complex symbols. Then several symbols are put together into one symbol vector. The symbol vector is multiplied with a ROT matrix modified according to the present aspect of the present invention in the ROT multiplication unit 9'. Figure 12 shows a ROT multiplication unit modified according to the present aspect of the invention. Note: the matrix A is still an oblong matrix, the input data are represented by a row (and not by a vector as it is the case in the preceding figures). Therefore the ROT matrix now has more columns than rows. Generally, when the input data are represented as a row vector, the ROT matrix has more columns than rows, and when the input data are represented as a column vector, the ROT matrix has more rows than columns. Figure 13 once again shows a matrix 40 which is a matrix reconstructed from a convolution coding matrix. The matrix A (reference sign 40 in Figure 13) is then divided into three submatrices A 0 , A 1 , A 2 (see Figure 14) which three submatrices A 0 , A 1 , A 2 are combined together horizontally. The elements a 0 , a 1 , a 2 of the convolutional coding matrix A (reference sign 40 in Figure 13) respectively represent terms of polynomials of a convolution function. The terms cannot only be binary values (e.g. -1, 1), but also real and complex values. The multiplication of the input symbol vector by the matrix A corresponds to the well-known convolution coding operation using a shift register as it is schematically represented in Figure 15. Instead of shifting input symbols, as it is the case according to the well-known convolution coding procedure, the terms (elements of the matrix A) representing polynomials of the convolution function are already shifted in each column vector (see Figure 15). Instead of taking a logical EXOR as it is the case in the known convolution coding, according to the present invention the products of respectively a term of the matrix and a symbol are summed along with the multiplication operation of the input symbol vector and the matrix A. All row vectors of the matrix 40 according to the present invention are orthogonal with each other so that the product of said matrix with a transposed matrix (complex conjugate transposed matrix) is a unit matrix as shown in Figure 16. All diagonal elements of the unit matrix as shown in Figure 16 are 1, whereas all other elements of said unit matrix are 0. Therefore the transposed matrix can be used in the unit 17' on the reception side to solve randomization and coding simultaneously. Choosing orthogonal polynomial terms, other ROT matrices can be generated which are respectively orthogonal to the original ROT matrix (see Figure 17). Therefore interference which is coded by orthogonal ROT matrices can be canceled. The multiplication of the received symbol vector with the transpose of the matrix used on the transmission side is as shown above one technique to solve simultaneously randomization and convolution coding. Another technique directed on said object is the so-called Trellis technique, which will now be explained with reference to Figures 18 to 21. According to the Trellis technique, the elements of the received ROT transformed symbol are summed up as shown in the second equation of Figure 18 to generate an equivalent vector of xA . The generated equivalent vector xA is composed of n elements s 0 , s 1 , ...s n-1 representing respectively a summation result. Using said elements s 0 , s 1 , ...s n-1 of the equivalent vector xA a state matrix as shown in Figure 19 is generated. If the modulation scheme is QPSK the number of states 4 k-1 , wherein k is the constraint length. Then the path metrics (Hamming distances) of the state matrix using the symbols of equivalent vectors are calculated. Said calculated path metrics are summed up with original state metrics. The original Trellis state matrix is shown in Figure 21. Respectively the two accumulated metrics of paths leading to a new state (see Figure 19) are then compared. Finally the received decoded symbol is decided to be the path having the larger path matrix and therefore the higher reliability. With other words, according to the Trellis technique as shown in Figure 18 to 21, a Viterbi decoding operation is effected using soft decision information, as the metric is calculated by measuring the distance between the received actual symbol and estimated places generated from each state transition (see Figure 20). To summarize, the oblong ROT matrix can also be used for convolutional coding/decoding. For example a Viterbi algorithm can be used solving the randomization by a multiplication with a transpose matrix or a Trellis decoding technique. Therefore, according to this aspect of the present invention, convolutional coding and the ROT matrix technique using oblong matrices is combined. As it is shown in Figure 11 the original channel coding can therefore be replaced the ROT multiplication operation, which stills keeps orthogonality with the interference signals.

Claims: An OFDM transmitter for the wireless transmission of information data, comprising means (9) for orthogonally transforming data blocks to be transmitted using a randomly generated orthogonal basis by multiplying a vector (x) which comprises data of one supplied data block with an oblong matrix hereinafter referred as R , means (10) for IFFT-transforming the randomly orthogonally transformed data blocks ( y ), and means for OFDM-modulating the IFFT-transformed data, wherein the matrix R is used which comprises n orthogonal columns, n being the number of data samples comprised in each of said data blocks, and the number ( M · n ) of rows of said matrix R is larger than the number ( n ) of said columns of said matrix R when representing the data samples of each data block as a column vector ( x ). An OFDM transmitter according to claim 1, wherein said OFDM transmitter comprises a modulator (8) which outputs data blocks (x) being supplied to said means (9) for randomly orthogonally transforming. An OFDM transmitter according to anyone of the preceding claims, wherein said OFDM transmitter comprises a convolutional encoder (9') which is implemented on the basis of the matrix R , which is obtained by dividing a convolutional coding matrix ( A ) into submatrices, whose elements are polynomials coefficients of a convolution function. An OFDM receiver for receiving wirelessly transmitted information data, comprising means for OFDM-demodulating the received data, means (16) for FFT-transforming the OFDM-demodulated data, and means (17) for orthogonally transforming the FFT-transformed data supplied in data blocks using a randomly generated orthogonal basis by multiplying a vector ( y ) which comprises data of one supplied data block with the transpose matrix ( R T ) of a matrix hereinafter referred as R , wherein said matrix R comprises n orthogonal columns, n being the number of data samples comprised in each of said data blocks, and the number of rows of said matrix R is larger than the number of said columns of said matrix R when representing the data samples of each data block as a column vector ( y ). An OFDM receiver according to claim 4, comprising means (17') for executing an inverse random orthogonal transformation and performing a convolutional decoding of data blocks ( y ) received by applying a Trellis decoding technique. An OFDM receiver according to claim 5, wherein said means (17') for executing an inverse random orthogonal transformation and performing a convolutional decoding of data blocks received comprise means for calculating an equivalent vector ( xA ) of a received symbol, means for generating a Trellis state matrix ( S ) on the basis of elements of means for calculating path metrics and adding up the calculated path metrics with original state metrics, and means for deciding the decoded symbol by comparing the path metrics of the two paths leading respectively to a new state of the Trellis state matrix ( S ). A transmitting system, comprising a plurality of base stations (BS j ) and a plurality of mobile stations (MS i ), wherein each mobile station (MS i ) and base station (BS j ), respectively, comprises a transmitter according to anyone of the claims 1 to 3 and a receiver according to anyone of the claims 4 to 6. An OFDM transmission method for wirelessly transmitting information data, the method comprising the following steps: orthogonally transforming (9) data blocks to be transmitted using a randomly generated orthogonal basis by multiplying a vector ( x ) which comprises data of one supplied data block with an oblong matrix hereinafter referred as R , IFFT-transforming (10) the randomly orthogonally transformed data blocks (y), and OFDM-modulating the IFFT-transformed data, wherein a matrix R is used which comprises n orthogonal columns, n being the number of data samples comprised in each of said data blocks, and the number ( M · n ) of rows of said matrix R is larger than the number ( n ) of said columns of said matrix R when representing the data samples of each data block as a column vector ( x ). A method according to claim 8, comprising the step of modulating (8) data to output data blocks ( x ) being supplied to the step of randomly orthogonally transforming (9). A method for receiving wirelessly transmitted OFDM-modulated data, the method comprising the following steps: OFDM-demodulating the received data, FFT-transforming (16) the OFDM-dernodulated data, and orthogonally transforming (17) the FFT-transformed data supplied in data blocks using a randomly generated orthogonal basis by multiplying a vector ( y ) which comprises data of one supplied data block with the transpose matrix ( R T ) of a matrix hereinafter referred as R , wherein said matrix R comprises n orthogonal columns, n being the number of data samples comprised in each of said data blocks, and the number of rows of said matrix R is larger than the number of said columns of said matrix R when representing the data samples of each data block as a column vector ( y ). A method for performing a convolutional encoding of digital data blocks, comprising method steps according to claim 8 or 9, wherein the matrix R used for orthogonally transforming data blocks ( x ) to be transmitted is obtained by dividing a convolutional coding matrix ( A ) into submatrices, whose elements are polynomials coefficients of a convolution function, such that a matrix operation step applying the matrix R to a data vector ( x ) provides both for a random orthogonal transformation and a convolutional encoding, wherein the elements of the convolution code matrix ( A ) are polynomials coefficients of a convolution function. A method for decoding digital data blocks encoded according to claim 11, comprising the steps of executing (17') an inverse random orthogonal transformation and performing a convolutional decoding of data blocks ( y ) received by applying a Trellis decoding technique. A method according to claim 12, wherein said step (17') of executing an inverse random orthogonal transformation and performing a convolutional decoding of data blocks received comprises the steps of calculating an equivalent vector ( xA ) of a received symbol, generating a Trellis state matrix ( S ), calculating path metrics and adding up the calculated path metrics with original state metrics, and deciding the decoded symbol by comparing the path metrics of the two paths leading respectively to a new state of the Trellis state matrix ( S ).

Inventors: IZUMI SEIICHI, IZUMI, SEIICHI, Izumi, Seiichi Sony International (Europe) GmbH
Applicants: SONY INT EUROP GMBH, SONY INTERNATIONAL (EUROPE) GMBH
Application year: 1998
Main classification: H04L27
IPC codes: H04B15, H04J11, H04L27, H03M13, H04L5