VIBRATIONAL TRANSDUCER

Abstract: A vibrating tranducer or alarm for a pager, cellular telephone and the like, includes a single coil wound in a longitudinal direction to enclose a chamber extending in the longitudinal direction; a planar substrate, bonded to an outer wall formed by the coil; a switching power source, operatively coupled to the coil, for producing an oscillating magnetic field within the chamber, and an eccentric weight rotor assembly extending within the chamber, where the rotor assembly includes a permanent magnet that provides a rotational force to the rotor assembly when acted upon by the oscillating magnetic field.

Description: VIBRATIONAL TRANSDUCER CROSS REFERENCE TO RELATED APPLICATIONS This application claims priority under 35 U.S.C. §119 from Provisional Application Ser. No. 60/051,737 filed July 3, 1997, the entire disclosure of which is incorporated herein by reference. COPYRIGHTED MATERIAL A portion of the disclosure of this patent document contains material which is subject to copyright protection. The copyright owner has no objection to the facsimile reproduction by anyone of the patent document or the patent disclosure, as it appears in the PTO patent files or records, but otherwise reserves all copyright rights whatsoever. BACKGROUND The present invention relates to personal communication devices, and more particularly, to a vibrational transducer or vibrating alarm for use with personal communication devices. Vibrating alarms for use with personal communication devices are well known in the art. Many of these alarms comprise conventional motors having an eccentric weight attached to the rotor shaft. Accordingly, when the motor is activated, the rotation of the rotor shaft and corresponding rotation of the eccentric weight causes vibration within the personal communication device that is detected by the holder of the device. A disadvantage with conventional eccentric weight motors is that they are not specifically designed for mass production. In particular, several manual labor steps are required to assemble the device. For example, the most popular conventional vibrating motors require three coils, each of which must be soldered to the associated leads by manual labor. Additional disadvantages with conventional vibrating motors is that they are not surface mountable, i.e., that they are not specifically adapted to be surface mounted onto a circuit board of a personal communication device. For example, the most popular conventional vibrating motors require a specialized bracket which must first be mounted to the personal communication device, a male connector component which must be attached to the ends of the motor's lead wires, and a corresponding female connector which is mounted to the communication device's circuit board. First, the bracket must be mounted within the communication device, then the female connector is mounted to the circuit board, then the male connector is coupled to the wires of the motor, and finally, in an assembly process, the motor is installed into the bracket and the female and male connectors are mated. Accordingly, a need exists for a vibrating alarm for use with a personal communication device which substantially reduces manual assembly requirements, which is specifically designed to be surface mounted onto a printed circuit board of a personal communication device, and which minimizes the energy requirements for operating the device. SUMMARY The present invention is a small vibrating motor for use with a personal communication device that comprises a rotor assembly mounted within a single coil wound to form a chamber therewithin for receiving the rotor assembly. The rotor assembly is mounted within the chamber by upper and lower bearing assemblies. A semi-cylindrical, or half-donut shaped magnet is coupled to the rotor assembly so that when an alternating magnetic field is supplied by the coil, the magnet is caused to move and rotate within the coil. The half donut-shaped magnet provides an eccentric weight, such that rotation of the rotor assembly within the coil causes the motor to vibrate. Of course, other eccentrically shaped magnets may also be utilized in place of the half donut-shaped magnet. The coil and rotor assembly is contained within a housing that is specifically designed to be surface mounted or PC mounted to a circuit board. In a first embodiment, an H-bridge circuit is used to provide switched power to the motor, and a comparator circuit is used to sense the direction of motor generated Voltage (back-EMF). A microprocessor or microcontroller, operatively coupled to the H- bridge and comparator circuits, preferably uses the back-EMF signal to determine the appropriate driver input signals to apply to the H-bridge circuit. Therefore, the EMF comparator circuit is used to control the commutation in the motor. Accordingly, one aspect of the present invention provides a vibrating transducer comprising a coil wound in a longitudinal direction to enclose a chamber extending in the longitudinal direction; a switching power source, operatively coupled to the coil, for producing an oscillating magnetic field within the chamber; and a rotor assembly extending within the chamber, where the rotor assembly includes a permanent magnet and where the rotor assembly has center of mass located radially distal from its rotational axis. Another aspect of the present invention provides a communication device comprising a receiver component for receiving messages transmitted to the communications device, a processor operatively coupled to the receiver component for processing messages received by the receiver component, and a vibrating alarm operatively coupled to the processor where the vibrating alarm includes the small vibrating transducer described above. Yet another aspect of the present invention provides a vibrating alarm for a pager, cellular telephone and the like, comprising a single coil wound in a longitudinal direction to enclose a chamber extending in the longitudinal direction; a planar substrate, bonded to an outer wall formed by the coil; a power source, operatively coupled to the coil, for producing an oscillating magnetic field within the chamber; and an eccentric weight rotor assembly mounted within the chamber, where the rotor assembly includes a permanent magnet that provides a rotational force to the rotor assembly when acted upon by the oscillating magnetic field. Accordingly, it is an object of the present invention to provide a vibrating transducer for use with a personal communication device that significantly reduces manual labor requirements in manufacturing the transducer; it is a further object of the present invention to provide a vibrating transducer for use with a personal communication device that uses a single coil as opposed to several coils; it is a further object of the present invention to provide a vibrating transducer for use with a personal communication device that can be surface mounted to a printed circuit board; and it is a further object of the present invention to provide a vibrating transducer for a personal communication device that can transfer vibrational energy in any direction needed by simply mounting the transducer in a particular orientation. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a schematic, block-diagram representation of a personal communication device incorporating the vibrating transducer of present invention; Fig. 2A is an elevational, cross-sectional view of the vibrating transducer of the present invention (taken along line 2A-2A of Fig. 2B); Fig. 2B is a top, cross-sectional view of the vibrating transducer taken along line 2B-2B of Fig. 2A; Fig. 3A is a bottom, perspective view of the vibrating transducer of the present invention including pins, facilitating PC mounting; Fig. 3B is a bottom, perspective view of the vibrating transducer of the present invention including surface-mount pads, facilitating surface mounting; Fig. 3C is a bottom, perspective view of the vibrating transducer of the present invention including break-out wires, facilitating optional mounting methods; Fig. 4 is a schematic representation of H-bridge and comparator circuits for use with the present invention; Fig. 5 is a time versus Voltage diagram illustrating operation of the H-bridge and comparator circuits of Fig. 4; Fig. 6 is a flow diagram illustrating operation of the microcontroller or microprocessor of the present invention; Fig. 7 is a block-diagram representation of an alternate embodiment of the vibrating transducer; Fig. 8 is a schematic representation of an oscillator circuit for use with the embodiment of Fig. 7; Fig. 9 is a schematic representation of an NT one-shot multivibrator circuit for use with the embodiment of Fig. 7; Fig. 10 is a schematic representation of a PT one-shot multivibrator circuit for use with the embodiment of Fig. 7; Fig. 11 is a schematic representation of an oscillator charge-control circuit for use with the embodiment of Fig. 7; Fig. 12 is a schematic representation of an oscillator discharge-control circuit for use with the embodiment of Fig. 7; Fig. 13 is a time versus Voltage diagram illustrating operation of the motor control circuitry of Figs. 7-12; Fig. 14 is a block-diagram representation of a motor control unit in yet another embodiment of the present invention; Fig. 15 is a block-diagram representation of a motor control unit in yet another embodiment of the present invention; Fig. 16 is a block-diagram representation of a motor control unit in yet another embodiment of the present invention, incorporating a center-tapped coil; Fig. 17 is an elevational, cross-sectional view of a vibrating transducer incorporating the center-tapped coil of Fig. 16; Fig. 18 is a time versus Voltage diagram illustrating operation of the motor control circuitry of Figs. 14 and 16; Fig. 19 is a circuit diagram for the microcontrollers of Figs. 14 and 16; Fig. 20 is a circuit diagram for a single-input, swept-frequency H-bridge driver for use with the present invention; Fig. 21 is a circuit diagram for a single-input, swept-frequency dual-transistor driver for use with the present invention; Fig. 22 is a time versus Voltage diagram illustrating operation of swept-frequency driver circuitry for use with the circuits of Figs. 20 and 21 ; Fig. 23 is a circuit diagram for a microcontroller for generating the driver signal of Fig. 22; Fig. 24A is a cross-sectional top plan view of yet another embodiment of the vibrating transducer, taken along lines 24A-24A of Fig. 24B; Fig. 24B is a cross-sectional elevational view of the embodiment of Fig. 24A, taken along lines 24B-24B of Fig. 24A; Fig. 25A is a perspective, cut-away view of yet another embodiment of the vibrating transducer; and Fig. 25B is an elevational, cross-sectional view of a longitudinal portion of the embodiment of Fig. 25A. DETAILED DESCRIPTION As shown in Fig. 1, a cellular telephone, pager or other type of personal communication device will typically include a central processor 20 such as a microprocessor, microcontroller or other similar processing device; a receiver 22 such as an RF antenna, an infrared sensor, or other related reception device; an output device 24 such as an LCD or LED display component and/or a speaker component; and a power supply 26, such as a battery, a solar cell, or any other known means for providing power to the various components of the personal communication device. Such components are known to those of ordinary skill in the art and will therefore not be discussed in significant detail herein. Generally, the processor 20 receives information transmitted to the personal communication device from the receiver 22 and relays that information to the user of the personal communication device by controlling the output device 24. The personal communication device will also include a vibrating transducer 28 of the present invention for alerting a user of the device of an incoming message, for example. The vibrating transducer 28 of the present invention includes a motor 30, and a switched power source 32. As will be described in further detail below, the motor 30 includes a coil 33 and a rotor assembly 34 extending near the coil and having a center of mass located radially distal from its rotational axis. Furthermore, the vibrating transducer 28 also preferably includes a component or a circuit, such as a comparator 36, operatively coupled to the coil 33 for detecting the direction of travel of the rotor assembly 34. As shown in Figs. 2A and 2B, the coil 33 is wound in a longitudinal direction L to enclose a chamber 38 extending in the longitudinal direction L. Preferably, the coil 33 is layer-wound in the longitudinal direction L. The coil 33 is mounted to a substrate 40 and is also encased by a low-cost, molded plastic housing 42, which is also mounted to the substrate 40. The rotor assembly 34 includes a center hub 44, including a shaft 46 extending through the center of the rotor hub 44. The center shaft 46 extends between an upper end bearing 48 and a lower end bearing 50, which are in turn mounted, preferably by epoxy, to the coil 33 within the chamber 38. Rotor assembly 34 also includes an eccentric shaped magnet 52 mounted, preferably by epoxy, to the center hub 44. As shown in Figs. 2A and 2B, the magnet 52 is preferably semi-cylindrical, i.e., shaped as a half-donut, where its inner circumferential surface (hole) 55 is mounted to the center hub. As will be described in detail below, when a suitable magnetic field is produced by the coil 33, the rotor assembly 34 will rotate within the upper and lower end bearings 48, 50. The eccentric shape of the magnet 52 provides an eccentric weight, such that rotation of the rotor assembly 34 within the coil causes the motor 30 to vibrate. Preferably, the magnet 52 is a neodium/iron/boron-magnet stabilized with electroless nickel plate. The magnet 52 is magnetized in a direction parallel to its axis of symmetry (in the H direction). The end bearings 48, 50 are preferably grade 4203 poly (amide-imide), the shaft 46 is preferably a high-speed steel polished drill rod, the center hub 44 is preferably free machining brass, and the substrate 40 is preferably FR404 epoxy glass. Accordingly, the motor design is extremely simple, consisting of a rectangular coil 33 with a rotating, off-center magnet 52 therewithin. Since no external shaft is necessary, rotor assembly 34 can be completely contained within the confines of the coil 33. Operating force is transmitted to the outside housing 42 through the shaft 46 and bearing structures 48, 50. The substrate 40 is preferably a glass-epoxy printed-circuit-board material, which facilitates the mounting of associated driver circuitry thereon and also facilitates the inclusion of PC-mount pins 57 (see Fig. 3A), surface-mount pads 59 (see Fig. 3B), or wire leads 61 (see Fig. 3C) thereto. Driver circuitry for use with the present invention is described in detail below. The motor torque varies approximately as the sine of the angle between the longitudinal axis of the coil (which defines the direction of flux inside the coil) and the axis of symmetry of the magnet (the direction of magnetization H); thus, if the magnet is at rest and these axes are aligned, the torque is zero (0), and the motor cannot start. Torque is maximum when the magnet's axis of symmetry and the longitudinal axis of the coil are at 90°. As shown in Figs. 2A and 2B, a small, 0.001 inch thick strip 53 of nickel-iron alloy is therefore attached to the casing on one side of the coil 33 to position the magnet 52 so that, when power is off, the magnet's axis of symmetry and the longitudinal axis of the coil are at 90°, thereby facilitating maximum torque at startup. The strip 53 is preferably placed near or on a side of the coil which is in a plane parallel to the magnet axis of rotation, in such a manner as to minimize bearing loading/friction. As will be further described below, the power to the coil 33 is switched (reversed) when the magnet 52 reaches the extremity of travel (the extremity of travel will be the end of the coil when running, but during start-up, may or may not be the end of the coil), and a preferred method of determining when to switch the power is by detecting motion- generated or "back EMF" in the coil 33 using the comparator circuit 36. As shown in Fig. 4, in one embodiment, the switching power source 32 utilizes a conventional H-bridge circuit. Directional inputs A and B are provided by the central processor 20. As those of ordinary skill in the art will recognize, when input A is active, NPN transistor T3 is activated, causing PNP transistor T2 to activate, which in turn allows positive current to flow through T2, through the coil 33, through NPN transistor T3, to ground. Accordingly, activating input A, provides positive Voltage across the motor 30. Likewise, when input B is activated by the central processor, NPN transistor T4 is activated, causing PNP transistor T1 to be pulled to active. Therefore, positive current flows through PNP transistor T1 , then through the coil 33, through NPN transistor T4, and then to ground. Accordingly, activating input B causes negative Voltage to be applied across the motor 30. Resistor R1 is coupled to the emitters of NPN transistors T3 and T4 and is used to lower the transitional/shoot through current spikes in the circuit. The individual values of the components of the H-bridge circuit of the first embodiment are given in the table below: Ref. Type Value/Type T1 PNP Transistor MPS751 T2 PNP Transistor MPS751 T3 NPN Transistor MPS651 T4 NPN Transistor MPS651 R1 Resistor 1 Ohm R2 Resistor 300 Ohm R3 Resistor 200 Ohm R4 Resistor 100 Ohm C1 Capacitor 47 micro-Farads D1 Schottky Diode SD103A Comparator circuit 36 is a conventional comparator circuit which will activate the output ("COMP OUT") 37 when the Voltage on motor lead ("MOTOR +") 41 is greater than the Voltage on motor lead ("MOTOR -") 43, and will likewise deactivate the COMP OUT 37 when MOTOR - 43 has a higher Voltage than MOTOR + 41. When the Voltage on MOTOR + is greater than the Voltage on MOTOR -, NPN transistor T5 will activate and NPN transistor T6 will deactivate, causing PNP transistor T7 to deactivate. Lack of Voltage out of divider circuit R9, R12 deactivates NPN transistor T8, which allows R11 to pull COMP OUT Voltage high. When the MOTOR - Voltage is greater than the MOTOR + Voltage, T6 will be active and NPN transistor T5 will deactivate. When T6 is active, PNP transistor T7 is in turn activated, allowing the divider circuit R9, R12 to activate NPN transistor T8, which pulls COMP OUT low. NPN transistors T9 and T10 and resistors R13 and R14 comprise a 100 micro-amp current source. The values of the first embodiment of the comparator circuit 36 are given in the table below (R- ΓRIM tπms the comparator input offset Voltage to 0, and is typically 115 K-Ohms): Ref. Type Value/Type T5 NPN Transistor 2N5089 T6 NPN Transistor 2N5089 T7 PNP Transistor 2N3906 T8 NPN Transistor 2N3904 T9 NPN Transistor 2N5089 T10 NPN Transistor 2N5089 R5 Resistor 1 K-Ohm R6 Resistor 3.0 K-Ohm R7 Resistor 10 K-Ohm R8 Resistor 100 K-Ohm R9 Resistor 1 K-Ohm R11 Resistor 10 K-Ohm R12 Resistor 10 K-Ohm R13 Resistor 5.1 K-Ohm R14 Resistor 2 K-Ohm ■" -RIM Resistor See above Operation of the H-bridge circuit 32 and the comparator circuit 36 is illustrated by reference to the Voltage versus timing diagram as shown in Fig. 5. The Voltage versus timing diagram of Fig. 5 depicts three signals, COMP OUT, MOTOR+ and MOTOR- in comparison to each other with respect to time. Activation of the A input into H-bridge circuit 32 by the central processor 20 can be seen by the substantially square peaks 45 in the MOTOR+ Voltage signal. Activation of the B input into the H-bridge circuit 32 by the central processor 20 can be seen as square peaks 47 in the MOTOR- Voltage signal. The sinusoidal portions 49 of each of the MOTOR* and the MOTOR- Voltage signals, represent the back EMF in the coil 33 caused by the moving (rotating) magnet 52 when neither of the A or B inputs into H-bridge circuit are activated. T w denotes the software delay time to allow for L/R decay (see functional block 60 of Fig. 6). Significant transitions of the comparator circuit 36 output, COMP OUT, are indicated by arrows at times T1 , T2, and T3 (13 msec, 28 msec and 49 msec). The edges of the "don't care" areas are not significant. T s is the total time from a COMP OUT edge to output transistor activation, and includes software latency (time for the microcontroller to execute the software and respond) and time for the electronics (transistors, etc.) to switch on. Because the magnet 52 will be rotating within the coil 33; during one 180° segment of its rotation, the magnet will have a velocity component in a first longitudinal direction with respect to the coil, and during the other 180° segment of its rotation, the magnet will have a velocity component in an opposite longitudinal direction with respect to the coil. As will be known to one of ordinary skill in the art, the back EMF signal in the coil 33 is directly dependent upon the product of magnet flux density and the magnet's velocity component due to the magnet's rotation within the coil 33. The central processor 20 is thus able to determine which longitudinal direction the magnet is traveling, with respect to the coil, by sampling the COMP OUT signal 37 from the comparator circuit. As discussed above, the central processor 20 uses the COMP OUT signal 37 to determine which of the appropriate driver input signals, A or B, to apply to the H-bridge circuit 32. Fig. 6 depicts a control algorithm for use by the central processor 20. At functional block 56, the motor is not operating, and to start the motor, the central processor 20, in functional block 58, will direct the H-bridge circuit to pulse the motor in a first direction, for a predetermined pulse time, either by activating the A input line or the B input line for the predetermined pulse time. In the present embodiment, the predetermined pulse time is 10 milliseconds. Advancing to functional block 60, the central processor will then delay for an appropriate L/R decay time. L/R decay time is the time required for the current in a circuit containing inductance (L) and resistance (R) to decay to an acceptable value. The L/R decay time for the present embodiment is 1 millisecond. In the loop formed by functional blocks 62 and 64, the central processor will sample the COMP OUT signal 37 from the comparator circuit 36 for a predetermined period of time or until the COMP OUT signal changes. In the present embodiment, the predetermined time to sample the COMP OUT signal in blocks 62 and 64 is 24 milliseconds. If, in functional block 62, the central processor determines that the COMP OUT signal had changed, the central processor will advance to functional block 66. But if a time-out occurred in functional block 64, before the COMP OUT signal changes, the central processor will advance to functional block 68. Typically a time-out will occur only in a situation where the first pulse delivered in functional block 58 failed to move the magnet; and therefore, the motor will need to be pulsed in the opposite direction. Accordingly, in functional block 68 the central processor toggles the pulse direction and returns to functional block 58 to cause the H-bridge circuit to pulse the motor in the opposite direction (i.e., if the A input line was originally activated, now the B input line will be activated). From functional block 58, the central processor returns to functional block 60. If, in functional block 62 the central processor had determined that the COMP OUT signal had changed, then in functional block 66, the central processor will determine, based upon the new value of the COMP OUT signal, which longitudinal direction (relative to the coil) that the magnet was traveling. If the COMP OUT signal indicates that the magnet was traveling in the reverse direction, the central processor will set the pulse direction to the forward direction and then return to functional block 58 to pulse the motor in the forward direction. However, if the COMP OUT signal indicates that the magnet was traveling in the forward direction, the central processor will advance to functional block 70 to set the pulse direction to the reverse direction. From functional block 70, the central processor returns to functional block 58 reverse direction. As will be apparent from the above, steps 58, 60, 62, 64 and 68 will repeat until the motor is started; and steps 58, 60, 62, 66, and 70 will repeat once the motor has started and until the central processor deactivates the motor. As shown in Fig. 7, another embodiment of the present invention uses a motor driver circuit having all transistors and no microcontrollers, making the circuit suitable for realization in the form of a single monolithic bipolar integrated circuit. The circuit utilizes an H-bridge driver 32' and a comparator 36' similar to the first embodiment above, however, the control algorithm as depicted in Fig. 6 is implemented in a form of an oscillator circuit 74, two monostable (one-shot) multivibrator circuits 76, 78, and oscillator control circuitry, 80, 82. The power supply is a single nickel cadmium (NiCd) cell with an output Voltage of 1.3VDC. The primary difference between the comparator 36' of the alternate embodiment of Fig. 7 and the comparator 36 of Fig. 4, is that the comparator 36' of the bipolar IC circuit uses a 1K resistor for R11, pulled up to 1.3 VDC. Also R6 is changed from 3.3 K-Ohm to 3.0 K-Ohm. As shown in Fig. 8, the oscillator circuit 74 generates the basic pulse outputs OSC A-out 86 and OSC B-out 88. These outputs, respectively, have well defined negative transition and positive transition. Low Voltage operation is accomplished by using a current source and sink to charge and discharge a 100 nanoFarad timing capacitor C2. The individual values of the components of the oscillator circuit 74 are given in the table below: Ref. Type Value Type T13 PNP Transistor 2N5087 T14 NPN Transistor 2N5089 T15 PNP Transistor 2N5087 T16 NPN Transistor 2N5089 T17 PNP Transistor 2N5087 T18 NPN Transistor 2N5089 R15 Resistor 1 K-Ohm R16 Resistor 51 K-Ohm R17 Resistor 2 M-Ohm R18 Resistor 200 K-Ohm C2 Capacitor 100 nF As shown in Fig. 9, the NT one-shot multivibrator circuit 76 translates the positive pulse of the OSC A-out 86 into a 7 millisecond square wave pulse at A-out 90. The NT one-shot multivibrator circuit 76 utilizes a 1.0 nanoFarad capacitor C4 and a one megaOhm resistor R20 to differentiate the OSC A-out signal 86 to sense the negative edge. When the negative transition occurs, the 68 nanoFarad capacitor C5 is discharged, and the output A-out 90 goes high. The output A-out 90 remains high while the current source, realized by transistors T21 , T22 and resistors R20, R22, charges capacitor C5. When capacitor C5, becomes charged, the current mirror transistor T22 turns off, and the output A-out 90 returns low. As shown in Fig. 10, operation of the PT one-shot multivibrator circuit 78 is identical to the NT one-shot multivibrator circuit 76 except an inverter T26 on the input, OSC B-out 88, makes the circuit 78 sensitive to the positive edge. The individual component values for the NT one-shot multivibrator circuit 76 and the PT one-shot multivibrator circuit 78 are given in the table below: Ref. Type Value/Type T19 NPN Transistor 2N5089 T20 NPN Transistor 2N5089 T21 PNP Transistor 2N5087 T22 PNP Transistor 2N5087 T23 NPN Transistor 2N5089 T24 NPN Transistor 2N3904 T25 NPN Transistor 2N5089 T26 NPN Transistor 2N5089 R20 Resistor 1 M-Ohm R21 Resistor 200 K-Ohm R22 Resistor 20 K-Ohm R23 Resistor 3.9 K-Ohm R24 Resistor 100 Ohm R25 Resistor 5.1 K-Ohm R26 Resistor 100 K-Ohm R27 Resistor 10 Ohm R28 Resistor 1 K-Ohm R29 Resistor 2 M-Ohm R30 Resistor 200 K-Ohm C4 Capacitor 1 nF C5 Capacitor 68 nF Figs. 11 and 12, respectively show the oscillator charge control and discharge control circuits 80, 82. The oscillator control circuits respectively charge or discharge the 100 nF oscillator capacitor C2 when the comparator circuit 36' senses the direction change in back-EMF of the motor. Since back-EMF is sensed only when the H-bridge circuit outputs are off, response is inhibited during drive pulses by INH A and INH B (see Figs. 9 and 10). Also the 2.2 nF delay timing capacitors C7, C9 increase inhibit time, to allow the motor winding current to decay to a negligible value. The individual values of the oscillator charge control circuit 80 are as follows: Ref. Type Value/Type T27 PNP Transistor 2N5087 T28 PNP Transistor 2N5087 T29 NPN Transistor 2N5089 T31 NPN Transistor 2N5089 T11 (see Fig. 7) PNP Transistor 2N5087 R31 Resistor 1 M-Ohm R32 Resistor 100 K-Ohm R33 Resistor 30 K-Ohm R34 Resistor 200 K-Ohm R35 Resistor 5.1 M-Ohm C6 Capacitor 1 nF C7 Capacitor 2.2 nF The individual values of the oscillator discharge control circuit 82 are as follows: Ref. Type Value Type T33 NPN Transistor 2N5089 T34 NPN Transistor 2N5089 T35 NPN Transistor 2N5089 T36 NPN Transistor 2N5089 T12 (see Fig. 7) NPN Transistor 2N5089 T38 NPN Transistor 2N5089 R36 Resistor 100 K-Ohm R37 Resistor 2 M-Ohm R38 Resistor 30 K-Ohm R39 Resistor 1 M-Ohm R40 Resistor 200 K-Ohm C8 Capacitor 1 nF C9 Capacitor 2.2 nF Operation of the motor driver circuitry shown in Figs. 7-12 is described in reference to the operational waveforms shown in Fig. 13. When the H-bridge 32' is off, the 1 K, 3.3K input dividers establish the zero-input Voltage to the comparator 36' at the common-mode Voltage V CM . Thus, the back-EMF generated Voltage (at MOTOR+ or MOTOR-) is measured as positive or negative with respect to V CM , which is 1.00 VDC for a 1.30 VDC supply. The differential-input comparator 36' (by definition) responds to the difference in Voltage between MOTOR+ and MOTOR-. Referring to the MOTOR+ waveform and progressing left to right, a negative-going lobe 94 of motor back-EMF is observed. This is the small, nearly sinusoidal waveform with a peak-to-peak magnitude of approximately 600 mV, and appears when the forward (A-Out) and reverse (B-Out) pulses are off. At this time, TO, the OSC CONTROL CHARGE waveform shows the oscillator timing capacitor C2 Voltage ramping as it is charging from the constant-current source. At time T1 (7 msec) the back-EMF becomes 0, the COMP OUT waveform switches high and the oscillator capacitor C2 charges rapidly turning on the forward H-bridge legs, as evidenced by the peak 96 on the MOTOR+ waveform. The forward pulse lasts for the NT one-shot time of about 7 msec, and turns of at time T2. The back-EMF pulse may again be observed on the MOTOR+ waveform as lobe 98. At time T3, the back-EMF goes through zero, causing the COMP OUT waveform to switch back to zero, which causes the oscillator control circuits to discharge the oscillator timing capacitor, and to turn the reverse pulse, B-Out, on. The reverse pulse lasts until time T4, where the back-EMF 100 is again apparent on the MOTOR+ waveform, first positive going, and then passing through 0 at time T5. Therefore, at time T5, the oscillator timing capacitor discharges rapidly. However, since the output (of the oscillator) is already in the negative state, a second reverse pulse is not generated (no positive transition is generated and the PT one-shot circuit does not put out a pulse). The actual motor speed is, however, determined by pulse. For the purposes of this disclosure, the wave-forms of Fig. 13 are shown in the proper time sequence for only the first cycle. As shown in Fig. 14, another alternate embodiment of the present invention 102 uses a swept-frequency motor driver circuit. The circuit utilizes a oscillator controller 104 to provide a switched input to the H-bridge circuit 32" at a frequency which is continuously swept from low to high. The low end of the frequency is low enough to start the motor when it is at rest. The frequency is thereafter swept up to increase the velocity of the motor. The unit is then turned off, allowing the rotor to coast. Then, the frequency is swept upward again, and the cycle repeats until power is removed. The use of this type of circuit eliminates the need for sensing the motor velocity (i.e., by using a comparator circuit or Hall Effect sensors). Turning off the unit between sweeps conserves energy and lowers battery drain. As shown in Fig. 15, another alternate embodiment of the present invention 106 utilizes Hall Effect switches 108 to sense the position of the rotor assembly 34, and a motor controller 110 to generate inputs to the H-bridge circuit 32" according, in part, to signals received back from the Hall Effect switches 108. A control algorithm is implemented by the controller that first starts rotation of the rotor assembly and then switches pulses to the drive coil 33 (commutates) in the proper sequence. The location of the Hall Effect switches 108 can be determined theoretically and/or by measurement. At a proper radius, axial flux of magnet 52 can produce a distinct positive peak in flux to activate the Hall-Effect switch 108. In practice, the best location was determined by moving a functioning Hall switch until proper operation was obtained. An example Hall Effect switch is an HAL 506UA, commercially available from ITT Semiconductors. The controller 110 preferably implements the following algorithm: 1. Apply forward Voltage to the coil 33. 2. Poll the Hall inputs for switch closure. 3. If no switch closure in 35 msec, turn off for a short time to eliminate crossover currents, and then apply a pulse in an opposite direction. Go to step 2, above. 4. If a Hall switch closes, turn off the pulse and wait for the switch to open. Then apply a pulse of proper polarity (determined by which switch was activated). Then go to step 2, above. As shown in Fig. 16, in another embodiment of the present invention 112, a center-tapped coil 114 can be utilized instead of the single coil of the prior embodiments. One side 114a of the coil will be coupled to a first switch 116a, while the other side 114b of the coil will be coupled to a second switch 116b. The center point of the coil 114 will be coupled to ground 120. When the switch 116a is activated by a controller 118, the first side 114a of the coil will be energized at a first polarity, and when the switch 116b is activated by the controller 118, the other side 114b of the coil will be energized at an opposite polarity. A control algorithm, such as a swept frequency algorithm, may be utilized to control the activation of the switches 116a, 116b. Referring to Fig. 18, the controller 104 of the circuit shown in Fig. 14 or the controller 118 of the circuit shown in Fig. 16 is programmed to switch outputs Drive A and Drive B on and off (active low) in a swept frequency. The outputs sweep from a half-period of 50 msec (10 Hz) to half-period of 6.8 msec (74 Hz). Motor pulsing time is 412 msec and off time is 308msec, totaling 720 msec for a sweep repetition rate of 1.4 times per second. The controllers 104, 118 are preferably a Microchip PIC12C508 microcontroller, with a circuit diagram as shown in Fig. 19. Source code for operating the controllers to provide the swept frequency output is appended hereto. The source code has a jump table which determines half-period times, approximately 200 usec per count (counts go from 1 to 256, 256 being indicated as 0). Thus, OFAH (the first value) is 250 * 0.2, or 50 msec and 22H (the last value) is 34 * 0.2, or 6.8 msec. The values between these two limits are chosen to give an exponential sweep envelope. The jump table has a total number of entries (40) defined by NUM_PULSES, and the number of half-pulses (34) is defined as ON_PULSES. A fixed off time between pulses of approximately 37usec is implemented in the software code to eliminate transition/shoot-through currents. As shown in Fig. 17, the functionality of the center-tapped coil 114 of Fig. 16 can be met utilizing a single bifilar wound coil 114', which is two insulated wires 114a', 114b' bonded together in parallel to form a discrete bifilar wire, which is then layer- wound in a longitudinal direction to enclose a chamber 38'. Within the chamber 38', the rotor assembly 34 is mounted for rotation. At one end of the bifilar coil 114', a first wire 114a' is operatively coupled to the first switch 116a and the second wire 114b' is operatively coupled to ground 120. At the other end of the bifilar coil 114', the other end of wire 114a' is coupled to ground 120 while the other end of wire 114b' is coupled to the second switch 116b. A suitable bifilar wire for use with the present invention is commercially available from MWS Wire Industries. As discussed above, the embodiments of Figs. 14 and 16 utilize dual-input swept frequency driver circuits. It is also within the scope of the invention to utilize a single- input swept frequency driver circuit as shown in Figs 20 and 21. Fig. 20 represents an H-bridge, single-input swept frequency driver circuit. The magnet preferably has a 5mm radius and the coil is preferably 3 layers of #33 AWG wire, having a resistance of 4.3 Ohms. The individual values of the H-bridge, single-input swept frequency driver circuit are as follows: Ref. Type Value Type T39 NPN Transistor BCX70 T40 PNP Transistor BCX17 T41 NPN Transistor BCX19 R41 Resistor 10 K-Ohms R42 Resistor 22 K-Ohms R43 Resistor 100 Ohms Fig. 21 represents a dual-switch, single-input swept frequency driver circuit. The magnet preferably has a 5mm radius and the coil is preferably 4 layers of #35 AWG bifilar wire and having a resistance of 5.8 Ohms per coil. The individual values of the dual-switch, single-input swept frequency driver circuit are as follows: Ref. Type Value/Type T42 NPN Transistor BCX70 T43 PNP Transistor BCX17 R44 Resistor 10 K-Ohms R45 Resistor 22 K-Ohms R46 Resistor 100 Ohms Referring to Fig. 22, the controller of the circuits shown in Figs. 20 and 21 is programmed to switch output Drive A (active low) in a swept frequency. The output starts with 10 half-cycles at 16.6 msec (30Hz), then sweeps to a half-period of 6.8 msec (74 Hz). Motor pulsing time is 418 msec and off time is 310msec, totaling 728 msec for a sweep repetition rate of 1.4 times per second. As shown in Fig. 23, the controller is virtually identical to that of Fig. 19, except that the GP1 output line is not used. The design of software for producing the swept frequency signal shown in Fig. 22 will be apparent to one of ordinary skill in the art. Figs 24A, 24B and 25A, 25B illustrate that there are many ways to fashion a rotor assembly of the present invention that includes a permanent magnet and a center of mass positioned distal from the rotational axis. As shown in Figs. 24A and 24B, in another alternate embodiment of the present invention 122, the alternate rotor assembly 124 utilizes a rectangular magnet 126 mounted with epoxy to a shaft 128. The coil 33 is mounted to a substrate 40 of glass-epoxy printed-circuit-board material. The magnet 126 provides the eccentricity of the motor by having its center of mass positioned radially distal from the shaft 128. As shown in Figs. 25A and 25B, in yet another alternate embodiment of the present invention 130, a substantially cylindrical magnet 132 is mounted for rotation within a coil 134 wound to form a cavity 136 therein. The rotor bearings 138 are mounted to the magnet on a rotational axis 140 which is off-center with respect to the magnet 132, and therefore, the magnet's center of mass will be positioned radially distal from the rotational axis 140 provided by the rotor bearings 138. Source code for operating the controller of Fig. 19, discussed above is as follows: c : \mplab\upl2c508 . inc Copyright 1998 John L. Myers Printed 20 : 41 24 Mar 9E * * * * * * * * **** * * * *** * * * * * * * * * * * * ** * filename υpl2c508.inc * * header file for PIC 12C508 * * by John L. Myers 9706281148 * * ** * * *************************** ; register definitions .*** * **************************** w EQU H'0000' ; working register F EQU H'0001' ; file register . ** * * ***** * * ** * * ** * ** * * ** * ** * ** ** ; * special registers * . ** * ***** *** *** **** ** * INDF EQU H 0000 indirect file register MRO EQU H 0001 timer 0 PCL EQU H 0002 program counter low byte STATUS EQU H 0003 status register STATUS bits * ** * * ****** * *********** * ******** R -0 RW-0 RW-0 R-l R-l R -x RW-x RW-x GP UF| I PAO I TO_ PD I Z I DC I C 0 GPWUF EQU H'0007' GPIO reset bit (1 = wake up from sleep) PAO EQU H'0005' page select (0 for 12C508) Tθ_ EQU H'0004 1 WDT time-out PD_ EQU H'0003' power-down Z EQU H'0002' zero DC EQU H'0001' digit carry C EQU H'OOOO' carry FSR EQU H'0004 1 file-select register/ indirect mem pointer FSR bits *** *** * *********** * ************* 1 1 1 RW-x RW-x RW-x RW-x RW-x IFSR4 FSR3 |FSR2 |FSR1 |FSR0 * ** ***************************** c : \mplab\upl2c508. inc Copyright 1998 John L. Myers Printed 20:41 24 Mar 98 OSCCAL EQU H'0005' ; oscillator calibration register OSCCAL bits ******************************** CAL7 EQU H'0007' CAL6 EQU H'0006' CAL5 EQU H'0005' CAL4 EQU H'0004' .********** * ********************* GPIO EQU H'0006' ; general purpose I/O register GPIO bits *** ** ** * ******************** **** RW-x RW-x RW-x RW-x RW-x RW-x GP5 GP4 GP3 GP2 GP1 GPO GP5 EQU H'0005' GP4 EQU H'0004' GP3 EQU H'0003' GP2 EQU H'0002' GP1 EQU H'0001' GPO EQU H'0000' ; TRIS bits . ******** * * 0 control for GPIO, 1 = input, 0 = output, write with TRIS f ******************************** * end special registers * ** ******* * **************** c : \ plab\upl2c508. inc Copyright 1998 John L. Myers Printed 20:41 24 Mar 98 OPTION bits ******************************** W-l W-l W-l W-l W-l W-l W-l W-l GPWU_|GPPU_|T0CS |T0SE PSA j PS2 j PS1 I PSO GPWU_ EQU H'0007 wake up on pin change (GPO, GPl, GP3 ) GPPU_ EQU HO006 enable weak pull-ups (GPO, GPl, GP3 ) TOCS EQU H'0005 TO clock source 0 for int clock) TOSE EQU FT 0004 TO source edge (0 for inc on L>H) PSA EQU H'0003 prescaler assignment (0 assigns to TO) PS2 EQU H'0002 prescaler setting (011 for div by 16) PS1 EQU H'0001 current design uses 4 MHz INTRC PSO EQU H'0000 divide by 2 Λ (n+l) for TMRO, 2 Λ n for WDT . * *** * *** * * * ***** * ***** * * ** **** * * ; RAM definition . * ******* * * * ***** * * * ***** * * * ** * * * _MAXRAM H'OOIF 1 ; . * **** * *** **** **** * * * ***** * **** * * Configuration Bits ** ** * *** * * ** ** * * **** *** ** * ** * * ** _MCLRE_ON EQU H'OFFF' _MCLRE_OFF EQU H' 0FEF ' _CP_ON EQU HOFF7' _CP_OFF EQU H'OFFF' _WDT_ON EQU H'OFFF' _WDT_OFF EQU H'OFFB' _LP_OSC EQU H ' 0FFC ' _XT_OSC EQU H' 0FFD' _IntRC_OSC EQU H'OFFE' _ExtRC_OSC EQU H'OFFF' .***************** * ********* * ** * * ; define reset vector .******************************** RESET EQU H'OIFF' ; roll over to H'OOOG' with OSCCAL ********************************* * ****** *** *************** * end PIC 12C508 header * ** * * ** **** *************** c : \mplab\ddrvhOyy . sm Copyright 1998 John L . Myers Printed 20 : 42 24 Mar 98 * * * * * * * ** * * * * * * * * * * **** * * * **** * * * filename ddrvhOyy.asm * * header file for ddrivexx.asm * * by John L. Myers 9803172240 * * * * ** * * ** ****** ** ****** * ******** option register initialization **** * ** ****** **** ***** ** * * **** * OPTION bits ****** * ** ** ******* *** *** * *** *** ** W-l W-l W-l W-l W-l W-l W-l W-l GPWU_ EQU H' 0007 wake up on pin change (GPO, GPl, GP3 ) GPPU_ EQU H' 0006 enable weak pull-ups (GPO, GPl, GP3) TOCS EQU H' 0005 TO clock source (0 for int clock) TOSE EQU H 1 0004 TO source edge (0 for inc on L>H) PSA EQU H' 0003 prescaler assignment (0 assigns to TO) PS2 EQU H' '0002 prescaler setting (011 for div by 16) PS1 EQU H '0001 current design uses 4 MHz INTRC PSO EQU H '0000 divide by 2 Λ (n+l) for TMRO, 2 Λ n for WDT OPT_INI EQU H'0083' ; . ********* GPIO configuration ****** ** ** *** *** ** * **** * ****** ** DRVR_ DRVF_ > > DRVR_ EQU H'0001' driver output reverse, active low DRVF_ EQU H'OOOO' driver output forward, active low GPIO_CFG EQU H'0008' general purpose port I/O configuration ****** * * **** *** ************ * **** c : \mplab\ddrvhOyy . asm Copyright 1998 John L . Myers Printed 20 : 42 24 Mar 98 ; * user registers * . * * * * * * * * * * * * * * * * * * CTRO EQU H 0007 program counter 0 CTR1 EQU H 0008 program counter 1 T_OFFSET EQU H 0009 look-up table offset ON_COUNT EQU H 000A counter for on pulses * ** **** * ************************ configuration register initialization ** ******** * *** * ***** * **** ** *********** CONFIGURATION bits (12) *** ******* * ********* * ** * ******** CP_ WDTE FOSCl FOSC0 MCLRE EQU H 0004 MCLR_ pin enable CP_ EQU H 0003 code protect negative enable WDTE EQU H 0002 watch dog timer enable FOSCl EQU H 0001 00 = LP oscillator 01 = XT oscillator FOSCO EQU H 0000 10 = int RC osc 11 = ext RC osc *** * *** * **** ** * * ** * **** ** ******* miscellaneous ******* *** * **** * ** ** ** *** ** * ** ** NUM_PULSES EQU H'0028' number of look-up table entries, even ON_PULSES EQU H'0022' number of on pulses < above * **** * * * **** ******** * **** * * ** *** *** *** * ***** * * * * * ******* * end of hdrive header * ************************ c : \mplab\ddrvsOyy . asm Copyright 1998 John L. Myers printed 21 : 09 24 Mar 98 .*********************************** ; * ddrivexx. asm page 0 subroutines * .★A********************************* ORG H'OOOO' ; rollover from 12C508 reset vector .********************************** MOVWF OSCCAL ; use oscillator trim GOTO MAIN ; begin program * ********** ** *************** * * * * sweep half-period delay time *** ** *************************** DELAY get delay value from table . * ** * ** ********* ** ******* MOVF T_OFFSET, W CALL DELAY_TABLE implement the delay ************************- load counter MOVWF CTR1 ; load counter high byte LOAD_CTRl MOVLW 41H ; load counter low byte MOVWF CTRO cycles = T_HIGH * (T_LOW * 3 + 5), use T_LOW = 41H for 200 usec COUNT DECFSZ CTRO, F GOTO COUNT NOP to make last cycles = 3 also DECFSZ CTR1, F GOTO LOAD_CTRl DECF T_OFFSET, F point to next table value DECF ON_COUNT, F count on pulses ; return to mam program RETLW 00H ******************************** c : \mplab\ddrvsOyy . asm Copyright 1998 John L. Myers Printed 21:09 24 Mar 98 ; table of hal: . ************** '_TABLE number of entries must be even ADDWF PCL, F jump to table entry NOP add NOP for automatic increment by 1 RETLW 00H 40, off times, 00H = 256 RETLW 00H 39 RETLW 00H 38 RETLW 00H 37 RETLW 00H 36 RETLW 00H 35 RETLW 22H 34, forward and reverse on times RETLW 22H 33 RETLW 22H 32 RETLW 23H 31 RETLW 23H 30 RETLW 23H 29 RETLW 24H 28 RETLW 24H 27 RETLW 25H 26 RETLW 25H 25 RETLW 26H 24 RETLW 27H 23 RETLW 27H 22 RETLW 28H 21 RETLW 29H 20 RETLW 2AH 19 RETLW 2BH 18 RETLW 2CH 17 RETLW 2DH 16 RETLW 2FH 15 RETLW 31H 14 RETLW 33H 13 RETLW 35H 12 RETLW 38H 11 RETLW 3BH 10 RETLW 3FH 9 RETLW 43H RETLW 49H 7 RETLW 51H 6 RETLW 5BH 5 RETLW 69H 4 RETLW 7EH 3 RETLW 0A3H 2 RETLW OFAH 1 , ************************ fill remaining space with NOP'S .******************************** FILL (NOP) , (0FF-$) GOTO MAIN * ***** ************************** end of subroutine page 0 : \Hiplab\ddrvpOyy . asm Copyright 1998 John L. Myers .******************************* ; * filename ddrvpOxx.asm * ;* hdrivexx.asm program page 0 * ; * by John L. Myers 9803032225 * .******************************* ; start program page 0 ORG H'0100' MAIN * ******************************** ; initialize . **** * ******************** MOVLW OPT_INI option settings -> option register OPTION MOVLW B' 00000011' initialize GPIO MOVWF GPIO MOVLW GPIO_CFG configure GPIO TRIS GPIO . *** ** ***** * * * *** *** * * ** ** drive vibrator, sweep the frequency ****** * * * ******* * ****** * * LOAD_CTRS start a sweep MOVLW NUM_PULSES load table pointer MOVWF T_OFFSET MOVLW ON_PULSES-l load on-pulse counter MOVWF ON_COUNT OUTPUT_DRIVE start a cycle MOVLW B'00000010' turn forward pulse on BTFΞC ON_COUNT, 7 turn off if > number of pulses MOVLW B'00000011' MOVWF GPIO CALL DELAY delay for forward pulse MOVLW B'00000011' output driver off-time MOVWF GPIO MOVLW 0AH load CTRO MOVWF CTRO COUNT_OFFl DECFSZ CTRO , F GOTO COUNT_OFFl NOP add 4 NOP's for = off times NOP NOP NOP MOVLW B'00000001' turn reverse pulse on BTFSC ON_COUNT, 7 turn off if > number of pulses MOVLW B'00000011' c : \mplab\ddrvpOyy . asm Copyright 1998 John L . Myers Printed 20 : 53 24 Mar 98 MOVWF GPIO CALL DELAY delay for reverse pulse MOVLW B'00000011 output driver of f -time MOVWF GPIO MOVLW OAH load CTRO MOVWF CTRO COUNT_OFF2 DECFSZ CTRO , F GOTO COUNT_OFF2 MOVF T_OFFSET, F test for end of sweep BTFSS STATUS , Z GOTO OUTPUT_DRIVE repeat the cycle GOTO LOAD_CTRS repeat the sweep . ** *** ******** * * ** ******** * ********** * *********** **** * * *** end MAIN fill remaining space with NOP'S **** * * *** **** **** *** ** **** ** ***** FILL (NOP), (H'01FF'-$); ************ ***** * * *** ** **** * ** ** PIC12C508 reset vector *** *** * ** * ******* *** ** ***** ***** MOVLW H ' 0CD0 ' unit #1 OSCAL trim value MOVLW H ' 0CC0 ' unit #2 OSCAL trim value MOVLW H ' 0CA0 ' unit #3 OSCAL trim value MOVLW H ' 0CC0 ' unit #4 OSCAL trim value *** *** * * ***** *** * ***** ** ******** end program page 0 Following from the above description, it should be apparent to those of ordinary skill in the art that, while the designs and operations herein described constitute several embodiments of the present invention, it is to be understood that the invention is not limited to these precise designs and operations, and that changes may be made therein without departing from the scope of the invention as recited in the following claims. What is claimed is:

Claims: 1. A vibrational transducer comprising: a coil wound in a longitudinal direction to enclose a chamber extending in the longitudinal direction; a switching power source, operatively coupled to the coil, for producing an oscillating magnetic field within the chamber; and a rotor assembly extending within the chamber, the rotor assembly including a permanent magnet, the rotor assembly having a rotational axis and a center of mass, the center of mass being located radially distal from the rotational axis. 2. The vibrational transducer of claim 1 , wherein: the rotor assembly includes a rotor; the magnet is mounted to the rotor; and the magnet has a center of mass located radially distal from the rotational axis. 3. The vibrational transducer of claim 2, wherein the magnet is substantially semi-cylindrical, the magnet having a hub, and the magnet is mounted to the rotor substantially along its hub. 4. The vibrational transducer of claim 3, wherein the magnet has an axis of symmetry and is magnetized in a direction parallel to the axis of symmetry. 5. The vibrational transducer of claim 4, wherein the rotor assembly is mounted to the coil within the chamber and the rotational axis is substantially perpendicular to the longitudinal direction. 6. The vibrational transducer of claim 5, further comprising: a magnetically susceptible object positioned in close proximity to the coil, so as to mis-align the magnet's axis of symmetry with a longitudinal axis of the coil when the switching power source is not active. 7. The vibrational transducer of claim 1 , wherein the switching power source includes: a controller for controlling production of switching power; and a comparator operatively coupled to the coil for detecting a longitudinal component of the magnet's travel, and for generating a directional signal indicative of the longitudinal component detected, the directional signal being sent to the controller; wherein the controller controls the production of switching power responsive to the directional signal. 8. The vibrational transducer of claim 7, wherein the controller is a microprocessor. 9. The vibrational transducer of claim 1 , wherein the rotor is journaled on a pair of sleeve bearings mounted within the chamber to opposing walls formed by the coil. 10. The vibrational transducer of claim 1 , further comprising a planar substrate material bonded to an outer wall formed by the coil. 11. The vibrational transducer of claim 10, wherein the substrate is an epoxy- glass substrate. 12. The vibrational transducer of claim 10, wherein the substrate is adapted to be surface mounted to a printed circuit board. 13. The vibrational transducer of claim 12, wherein the switching power source includes: a controller for controlling production of switching power; and a comparator operatively coupled to the coil for detecting a longitudinal component of the magnet's travel, and for generating a directional signal indicative of the longitudinal component detected, the directional signal being sent to the controller; wherein the controller controls the production of switching power responsive to the directional signal; wherein the controller and the comparator are mounted to the printed circuit board. 14. The vibrational transducer of claim 1 , wherein the switching power source includes: a controller for controlling the production of switching power; and a Hall Effect switch positioned near the magnet for detecting a position of the magnet within the coil and for generating a positional signal indicative of the magnet's position within the coil, the positional signal being sent to the controller; wherein the controller controls the production of switching power responsive to the positional signal. 15. The vibrational transducer of claim 1 , wherein the coil is a bifilar wound coil. 16. The vibrational transducer of claim 1 , wherein the switching power source includes a swept frequency driver circuit operatively coupled to the coil. 17. The vibrational transducer of claim 16, wherein the swept frequency driver circuit is a dual-input swept frequency driver circuit. 18. The vibrational transducer of claim 16, wherein the swept frequency driver circuit is a single-input swept frequency driver circuit. 19. The vibrational transducer of claim 1 , wherein the switching power source includes an H-bridge circuit operatively coupled to the coil and a controller operatively coupled to the H-bridge circuit. 20. A vibrating transducer for a pager, cellular telephone and the like, comprising: a single coil layer-wound in a longitudinal direction to enclose a chamber extending in the longitudinal direction; a planar substrate, bonded to an outer wall formed by the coil; a switching power source, operatively coupled to the coil, for producing an oscillating magnetic field within the chamber; and an eccentric weight rotor assembly extending within the chamber, the rotor assembly including a permanent magnet that provides a rotational force to the rotor assembly when acted upon by the oscillating magnetic field. 21. A communications device comprising: a receiver component for receiving messages transmitted to the communications device; a processor operatively coupled to the receiver component for processing messages received by the receiver component; and a vibrating alarm operatively coupled to the processor, the vibrating alarm including: a coil wound in a longitudinal direction to enclose a chamber extending in the longitudinal direction; a switching power source, operatively coupled to the processor and to the coil, for producing an oscillating magnetic field within the chamber responsive to a signal from the processor; and a rotor assembly extending within the chamber, the rotor assembly including a permanent magnet, the rotor assembly having a rotational axis and a center of mass, the center of mass being located radially distal from the rotational axis. 22. The communications device of claim 21 , further comprising a printed circuit board, wherein the processor and vibrating alarm are mounted to the printed circuit board.

Inventors: MYERS JOHN L, MYERS, JOHN, L.
Applicants: PROJECTS UNLIMITED INC, PROJECTS UNLIMITED, INC.
Application year: 1998
Main classification: G08B6
IPC codes: B06B1, G08B6, H02K3, H02K5, H02K7, H02K21