Multistage interference canceller for a code division multiple access communications system

Abstract: A multistage interference canceller and method for removing interference between users and multipath interference from received signals in multiple stages includes a plurality of despreading units which produce a received symbol vector and an estimated channel value, a synthesis unit which synthesizes the received symbol vector, an amplitude of the received symbol vector and the amplitude of the estimated value from each reverse spreading unit, and a decision unit which executes a hard decision and a soft decision according to a result of comparing the total amplitude of the received symbol vector and the total amplitude of the estimated channel value.

Description: BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a multistage interference canceller to be used in Code Division Multiple Access (CDMA) communication systems. More particularly, the present invention relates to digital mobile radio communication systems that use a Direct Sequence Code Division Multiple Access (DS-CDMA) communication system. More particularly, the present invention relates to a method of tentative decision in the multistage interference canceller. 2. Description of the Related Art The CDMA communication system is used for digital mobile radio communication systems in various countries. In this system, it is very important to improve the Signal-to-Interference Ratio (SIR) to decode received signals much more accurately. SIR can be adversely affected, for example, by interference from other users caused by the correlation between spreading codes. The multistage interference canceller, which generates and removes interference replicas from received signals in multiple stages, is generally expected to improve SIR. Figure 1 shows a configuration example of a conventional multistage interference canceller. In this example, stages 1 to m are linked longitudinally. Each stage has interference canceller units (ICU) (71) and synthesis units (72). The subscripts attached to the names of interference canceller units (71) ICU 1, 1 ∼ ICU 1,k , ICU 2, 1 ∼ ICU 2,k , ..., and ICU m, 1 ∼ ICU m,k correspond to stage numbers "1" to "m" and user numbers "1" to "k." In stage 1, received signal R 0 is input to interference canceller units ICU 1, 1 to ICU 1,k (which correspond to users). The interference canceller units then output interference replica signals S 1,1 to S 1,k and estimated interference residual signals d 1,1 to d 1,k . The synthesis unit (72) synthesizes estimated interference residual signals d 1,1 to d 1,k , removes them from received signal R 0 , and then outputs an error signal e 1 . In stage 2, error signal el from the synthesis unit (72) in stage 1 and interference replica signals S 1,1 to S 1,k from interference canceller units ICU 1,1 to ICU 1,k in stage 1 are input to interference canceller units ICU 2, 1 to ICU 2,k . Next, the interference canceller units output interference replica signals S 2,1 to S 2,k and estimated interference residual signals d 2,1 to d 2,k . The synthesis unit synthesizes estimated interference residual signals d 2,1 to d 2,k , removes them from error signal el input from stage 1, and then outputs error signal e2. Similarly, in stage m, error signal e m-1 (from the synthesis unit of the previous stage) and interference replica signals S m-1,1 to S m-1,k (from the interference canceller units of the previous stage) are input. The interference canceller units in stage m then output interference replica signals S m,1 to S m,k and estimated interference residual signals d m,1 to d m,k . Thus, the interference replica signals from which the interference between users and the multipath interference is removed can be obtained by the processing in each stage. Figure 2 shows the configuration of each interference canceller unit (71) shown in Figure 1. In this example, the interference canceller unit has a three-finger structure for rake (RAKE) synthesis. In Figure 2, "81" indicates a despread unit, "82" a synthesizer, "83" a decision unit, "84" a spreading unit "85" a synthesizer, and "86" a despreader. Also, "87" indicates an adder, "88" a multiplier, "89" channel estimation, "90" a multiplier, "91" an adder, and "92" a spreader. In the following explanation, symbol "^" represents an estimated value and symbol "*" represents a complex conjugate number. Error signal e m-1 from the previous stage (received signal R 0 if stage m is stage 1) and interference replica signal S m-1,k from the previous stage (zero if stage m is stage 1) are input to the despread unit (81) corresponding to the delay profile (path) of the received signal. The despreader (86) demodulates error signal e m-1 input from the previous stage in reverse according to a spreading code by despread. Note that in stage 1, received signal R 0 is input to the interference canceller in synchronization with the spreading code. The signal spread in reverse and demodulated by the above despreader is added to the interference replica signal input from the previous stage by the adder (87). Received symbol vector R i is then generated for path i. Received symbol vector R i for path is input to channel estimation (89), which outputs an estimated value ξ i ^ of the channel (phasing vector) of path i. Channel estimation (89) estimates the value by using a pilot symbols included in the received signal. For instance, the estimated value of the phasing vector may refer to an error in the signal phase or amplitude caused by phasing in a radio channel. The multiplier (88) multiplies received symbol vector R i by using complex conjugate number ξ i ^ * of estimated channel value ξ i ^ for weighting and phase compensation in proportion to the amplitude of estimated channel value ξ i ^. The synthesizer (82) synthesizes the signal output from the multiplier (88) corresponding to the path at the maximum ratio. The decision unit (83) temporarily evaluates synthesized received symbol vector £ R i ξ i ^ *. The synthesizer (83) outputs estimated information symbol vector Zs^ following hard decision of synthesized received symbol vector Σ R i ξ i ^ *. Output estimated information symbol vector Zs^ is input to the spreading unit (84). The multiplier (90) multiplies estimated information symbol vector Zs^ by estimated channel value ξ i ^ to generate interference replica signal S m,k for each path, then outputs the generated signal to the next stage. The adder (91) subtracts interference replica signal S m-1,k from interference replica signal S m,k for each path, then outputs the result to the spreader (92). The spreader (92) despreads the signal input from the adder (91) according to the spreading code, then outputs the spread signal for each path to the synthesizer (85). The synthesizer (85) synthesizes the signals input from the synthesizer (85) and outputs estimated interference residual signal d m,k . As the above operation is executed for users in more stages, error signal e m becomes closer to noise only, resulting in higher interference replica signal accuracy. Thus, a received signal (from which the interference between users and multipath interference is removed) can be obtained after rake reception processing using the error signal and interference replica signal in the final stage. Figure 3 shows an example of the signal space where the decision unit (83) executes hard decision of the received signal to which QPSK modulation is applied. Figure 3 shows in detail the first quadrant of the signal space enclosed by Q channels. In this example, received symbol vector Σ R i ξ i ^ * is subject to hard decision to confirm that it is estimated information symbol vector Zs^. The phase of received symbol vector Σ R i ξ i ^ * is compensated so that it becomes a normal vector signal. Estimated information symbol vector Zs^ is then output as the signal after tentative decision at a level equivalent to the total amplitude of estimated channel value ξ i ^. As previously described, the interference canceller unit corresponding to each user of a conventional multistage interference canceller has a decision unit (83). The decision unit (83) inputs and evaluates received symbol vector £ Ri ξ i ^ * output after rake synthesis by the synthesizer (82). The decision unit (83) evaluates estimated information symbol vector Zs^ (as shown in Figure 3) even when the signal level is abnormally high or low or the phase difference is large. The difference in phase or level occurs, for example some channel estimations use known pilot symbols which are periodically inserted every information data to estimate channel by interpolating the pilot symbols, to estimate value ξ i ^. The estimates value is also applied to information data, and is not always optimum for every received signal due to the varying influence of phasing and noise upon received signals. The influence of phasing and noise can cause received symbol vector Σ Ri ξ i * to differ significantly in level and phase from estimated information symbol vector Zs^ obtained by hard decision. If this occurs, the reliability of estimated information symbol vector Zs^ is lowered. If a less reliable estimated information symbol vector Zs^ is used to output interference replica and estimated interference residual signals to the next stage, the lowered capability of removing interference will cause a problem. Another example of a conventional interference canceller and interference cancellation method is to be found in the paper "Improved CDMA Performance using parallel interference cancellation" by D. Divsalar et al, 1994 IEEE MILCOM. CONFERENCE RECORD (CAT. NO. 94 CH 34009) PROCEEDINGS OF MILCOM '94, FORT MONMOUTH, NJ, USA, 2-5 OCT, 1994, pages 911-917 vol 3, XP-002134607 1994, NEW YORK, NY, USA, IEEE, USA ISBN; 0-7803-18 28-5. This paper refers to a general parallel interference cancellation scheme that significantly reduces the degradation effect of user interference but with a lesser implementation complexity then the maximum - likelihood technique. The scheme operates on the fact that parallel processing, which can be done in multiple stages, simultaneously removes from each user the total interference produced by the remaining most reliably received users accessing the channel. Tentative decision devices are used with different optimum thresholds at the multiple stages to produce the most reliably received data for generation and cancellation of user interference. Different types of decisions, hard, null zone and soft, are discussed. SUMMARY OF THE INVENTION It is an object of this invention to provide an interference canceller with greater capability to remove interference. Another purpose of this invention is to provide a highly accurate method of tentative decision in the interference canceller. To attain these and other objects the present invention has a decision unit for changing hard and soft decision according to a result of comparing the total amplitude of a received symbol vector the total amplitude of an estimated channel value, preset value and phase difference. BRIEF DESCRIPTION OF THE DRAWINGS Figure 1 shows the configuration of a conventional multistage interference canceller; Figure 2 shows the configuration of each interference canceller unit shown in Figure 1; Figure 3 shows an example of the signal space where a decision unit of the interference canceler unit executes hard decision of the received signal to which QPSK modulation is applied in the configuration shown in Figure 2; Figure 4 shows an example of the configuration using an interference canceller according to the present invention; Figure 5 shows another configuration example using the interference canceller of the present invention; Figure 6 shows the decision unit of Figure 5 and detailed operations executed thereby; Figure 7 shows an example of the signal space where the decision unit of the present invention executes hard, or soft decision for the received signal to which QPSK modulation is applied in the configuration shown in Figure 6; Figure 8 shows another example of detailed operations of the decision unit shown in Figure 5; Figure 9 shows an example of the signal space where the decision unit executes hard or soft decision for the received signal to which QPSk modulation is applied in the configuration shown in Figure 8; Figure 10 shows yet another example of the decision unit and detailed operations executed thereby; Figure 11 shows an example of the signal space where the decision unit executes hard or soft decision for the received signal to which QPSK modulation is applied in the configuration shown in Figure 10; Figure 12 shows still another example of the decision unit and detailed operations performed thereby; and Figure 13 shows an example of the signal space where the decision unit of Figure 12 executes hard or soft decision for the received signal to which QPSK modulation is applied. DETAILED DESCRIPTION OF THE PRESENTED EMBODIMENTS Figure 4 shows an embodiment of the interference canceller according to the present invention. Interference canceller units ICU 1 to ICU k corresponding to the users of each stage each include a despreading unit (1) having a despreader (6) and a channel estimation unit (7), and a first synthesis unit (2). These interference canceller units also have a decision unit (3) including a comparator (8) and a hard-soft decision unit (9) a spreading unit (4) with a spreader (10), and a second synthesis unit (5) coupled to the spreading unit 4. Like the interference canceller shown in Figure 2, this interference canceller of Figure 4 has multiple despreading units (1) and spreading units (4) that correspond to the delay profiles (multipaths) for received signals. Each despreading unit (1) receives error signal e m-1 and interference replica signal S m-1 input and error signal e m-1 stage. (If stage m is stage 1 of the multistage interference canceller, the error signal to be input is received signal Ro and the interference replica signal to be input is zero.) The despreader (6) despreads in reverse, demodulates, and outputs input error signal e m-1 according to a spreading code. The reversely spread, demodulated signal output from the despreader (6) becomes received symbol vector Ri after interference replica signal S m-1 is added. Channel estimation unit (7) calculates estimated channel value ξ i ^ from input interference replica signal S m-1 , and then outputs the signal. The theory of calculation is the same as that for the channel estimation shown in Figure 2. The complex conjugate number ξ i ^ * of estimated channel value ξ i ^ is multiplied by received symbol vector R i , then the result is synthesized by the first synthesizer 2 by rake synthesis. The synthesized received symbol vector Σ R i ξ i ^ * is output to the decision unit (3). The comparator (8) in the decision unit (3) compares the total amplitude Σ | ξ i ^ | of the estimated channel value ξ i ^ with the total amplitude Σ | Σ i ξ ^ * | of the synthesized received symbol vector output from the first synthesis unit (2). When the result of comparison is as follows, the hard-soft decision unit (9) in the decision unit (3) executes hard decision: Σ | ξ i ^ | ≤ Σ | R i ξ i ^ * | When the result of comparison is as follows, the hard-soft decision unit (9) in the decision unit (3) executes soft decision: Σ | ξ i ^ | > Σ | R i ξ i ^ * | Estimated information symbol vector Zs^ output from the decision unit (3) is multiplied by estimated channel value ξ i ^ in the spreading unit (4), then is output as the interference replica signal S m to the next stage. Interference replica signal S m-1 from the previous stage is also subtracted from interference replica signal S m , then the result is spread by the spreader (10) according to the spreading code. The spread signal is synthesized by the second synthesis unit (5), and output as an estimated interference residual signal d m . The interference canceller executes soft decision for a received symbol vector low in level and reliability. A decision error caused by soft decision can be reduced compared to that caused by hard decision, thus improving the interference replica signal accuracy. Figure 5 shows another embodiment of the interference canceller of the invention. In Figure 5, "11" indicates a despreading unit, "12" a first synthesizer (Σ), "13" a decision unit, "14" a spreading unit, "15" a second synthesizer(Σ), and "16" a despreader. Also, "17" indicates a channel estimation unit "19" a spreader, "20" an adder, "21" and "22" multipliers, "23" an adder, and "24" and "25" synthesizers (Σ). Error signal e m-1 from the previous stage (received signal R i if in stage 1) and interference replica signal S m-1,j from the previous stage (zero if stage m is stage 1) are input. Both signals are input to the despreading unit (11) corresponding to the delay profile (path i) of the received signal (as in the operation shown in Figure 2). The despreader (86) despreads an input error signal e m-1 in reverse according to the spreading code and demodulates the signal. Note that in stage 1, received signal R 0 is input to the interference canceller in synchronization with the spreading code. The adder (20) adds the signal spread in reverse and demodulated by the above despreader and the interference replica signal input from the previous stage to generate received symbol vector Ri for path i. Received symbol vector R i for path i is input to channel estimation (17), which outputs estimated value ξ i ^ of the channel (phasing vector) of path i. The multiplier (21) multiplies received symbol vector Ri by complex conjugate number ξ i ^ * of estimated channel value ξ i ^ for weighting and phase compensation in proportion to the amplitude of estimated channel value ξ i ^. The synthesizer (12) synthesizes the signal output from the multiplier (21) corresponding to the path at the maximum ratio (by rake synthesis). The synthesizer (24) synthesizes the absolute value of Σ R i ξ i ^ * to obtain the total amplitude Σ | R i ξ i ^ *| of the received symbol vector. The synthesizer (25) synthesizes estimated channel value ξ i ^ to obtain the total amplitude Σ | ξ i ^ *| of estimated channel value ξ i ^. Total amplitude Σ | R i ξ i ^ * | of the received symbol vector and total amplitude Σ | ξ i ^ *| of the estimated channel value are input to the decision unit (13). The decision unit (13) has a comparator and hard-soft decision unit. The comparator compares total amplitude Σ | ξ i ^ * | of estimated channel value ξ i ^ input from the synthesis unit (25) with total amplitude Σ | R i ξ i ^ * | of the synthesized received symbol vector input from the synthesis unit (24). When the result of comparison is as follows, the hard-soft decision unit executes hard decision: Σ | ξ i ^ | ≤ Σ | R i ξ i ^ * | When the result of comparison is as follows, the hard-soft decision unit executes soft decision: Σ | ξ i ^ | > Σ | R i ξ i ^ * | The soft decision compensates for the phase shift of the vector signal while maintaining a constant amplitude. Estimated information symbol vector Zs^ output from the decision unit (13) is input to the spreading unit (14) corresponding to the despreading unit (11). In the spreading unit (14), the multiplier (22) multiplies the input estimated information symbol vector Zs^ by estimated channel value ξ i ^ and outputs the interference replica signal S m,j to the next stage. Interference replica signal S m-1,j is subtracted from output interference replica signal S m,j , and the result is spread according to the spreading code by the spreading unit (19). Then the signal is synthesized by the second synthesis unit (15) and output as estimated interference residual signal d m,j to the next stage. Figure 6 shows an embodiment of the decision unit (13) of Figure 5. In Figure 6, "31" indicates a hard-soft decision unit, "32" a level comparator, and "12A" the received symbol vector Σ R i ξ i ^ * obtained after rake synthesis by the first synthesis unit (12). Also, "24A" indicates total amplitudes Σ | R i ξ i ^ *| of the received symbol vector obtained after rake synthesis by the synthesis unit (24), and "25A" the total amplitude Σ | ξ i ^ *| of the estimated channel value obtained by the synthesis unit (25). The decision unit (13) has the hard-soft decision unit (31) and the level comparator (32) connected to each other. The level comparator compares the total amplitude Σ | R i ξ i ^ *| of received symbol vector obtained by rake synthesis by the synthesis unit (24) shown in Figure 5 with total amplitude Σ | ξ i ^ *| of the estimated channel value obtained by the synthesis unit (25). The hard-soft decision unit (31) executes a hard or soft decision for received symbol vector Σ R i ξ i ^ * obtained after rake synthesis by the synthesis unit (12) shown in Figure 5 according to the result of comparison by the level comparator (32). When the result of comparison the comparator (32) is as follows, the decision unit executes hard decision. Σ | ξ i ^ | ≤ Σ | R i ξ i ^ *| When the result of comparison by the comparator (32) is as follows, the decision unit executes soft decision. Σ | ξ i ^ | > Σ | R i ξ i ^ *| The following describes how soft decision is executed in the embodiment shown in Figure 6. Figure 7 shows an example of the signal space where the decision unit (13) evaluates the received signal to which QPSK modulation is applied. When the result of comparison by the level comparator in the decision unit (13) is as follows, estimated information symbol vector Zs^ (compensated so that its vector signal is normal) becomes the output signal for tentative decision: Σ | ξ i ^ | ≤ Σ | R i ξ i ^ * | When the result of comparison by the level comparator in the decision unit (13) is as follows, soft decision is executed because the vector signal is low in level and reliability. Soft decision compensates for the phase shift of the signal while maintaining a constant amplitude. Σ | ξ i ^ | > Σ | R i ξ i ^ *| Compared with estimated information symbol vector Zs^ output after hard decision, estimated symbol vector Zs^ output after soft decision has a lower level. Thus, the adverse effect by decision error on subsequent stages can be reduced. Figure 8 shows another example of detailed operations related to the decision unit (13) shown in Figure 5. In Figure 8, "31a" indicates a hard-soft decision unit, "32a" a level comparator, and "12A" the received symbol vector Σ R i ξ i ^ * obtained after rake synthesis by the first synthesis unit (12). Also, "24A" indicates total amplitude Σ | R i ξ i ^ *| of the received symbol vector obtained after rake synthesis by the synthesis unit (24), and "25A" indicates total amplitude Σ | ξ i ^ *| of the estimated channel value obtained by the synthesis unit (25). Value A is preset as a value larger than the total amplitude Σ | ξ i ^ *| of the estimated channel value, and used as a reference value by the comparator (32a). Value A is preset in consideration of the maximum value, phasing, and interference that can be expected when a normal multipath signal is synthesized at the maximum ratio. Value A can also be determined on the experimental basis. The level comparator (32a) compares the total amplitude Σ | R i ξ i ^ *| of the received symbol vector, the total amplitude Σ | ξ i ^ *| of the estimated channel value, and preset value A to determine the order of collation. The level comparator then outputs the result of comparison. When the result of comparison by the level comparator (32a) is as follows, the hard-soft decision unit executes hard decision: Σ | ξ i ^ | ≤ Σ | R i ξ i ^ *| < A When the result of comparison by the level comparator (32a) is as follows, the hard-soft decision unit executes soft decision (i.e., compensated for the phase shift but maintains the amplitude): Σ | ξ i ^ | > Σ | R i ξ i ^ *| When the result of comparison by the level comparator (32a) is as follows, the hard-soft decision unit executes soft decision: A ≤ Σ | R i ξ i ^ * i | In the latter case, the decision unit 13 also multiplies the amplitude by a weight value so that the amplitude is less than Zs^ to obtain an estimated value. The weight value is determined by the number of users currently connected to the system. The weight value must be smaller when there are more users because the influence of decision error is larger. The above decision may be replaced with a decision method that assumes that the amplitude is a specific value less than "Zs^". The following explains detailed operations of hard and soft decision in the example shown in Figure 8. Figure 9 shows an example of the signal space where the decision unit (13) executes decision for the received signal to which QPSK modulation is applied. Assume that the result of comparison by the level comparator in the decision unit (13) is as follows (e.g., vector b in the figure): Σ | ξ i ^ | ≤ Σ | R i ξ i ^ *| < A In this case, estimated information symbol vector Z1^ (whose phase and amplitude is compensated to be normal) is the output signal used for tentative decision. Here, "Z1^" is equivalent to "Zs^". Next, assume that the result of comparison by the level comparator in the decision unit (13) is as follows (e.g., vector c in the figure): Σ | ξ i ^ | > Σ | R i ξ i ^ * | In this case, the phase of the signal is compensated while maintaining its amplitude (by soft decision) because the signal is low in level and reliability. Next, assume that the result of comparison by the level comparator in the decision unit (13) is as follows (e.g., vector a in the figure): A ≤ Σ | R i ξ i ^ * i | In this case, only the phase is compensated by soft decision as previously described, and the amplitude is multiplied by a certain weight value. The decision result has an amplitude value less than Z1^. As described before, the decision output signal can have an amplitude value (e.g., Z2^ in the figure) less than Z1^. Similar to the weight value described before, amplitude value Z2^ is determined by considering the number of users currently connected to the system. If the total amplitude of received symbol vector Σ R i ξ i ^ * obtained after the rake synthesis exceeds preset value A, the signal level is increased abnormally because noise is superimposed on the signal in equivalent phases and the reliability of the signal is low. When the level of the signal is lowered to the total amplitude of estimated channel value ξ i ^ and the signal is evaluated, decision error can be reduced. Thus, the cancellation characteristic can be improved. Figure 10 shows yet another embodiment of the decision unit (13) shown in Figure 5. In Figure 10,"31b" indicates a hard-soft decision unit, "32b" a level comparator, and "33" a zero output device. Also, "12A" indicates the received symbol vector Σ R i ξ i ^ * obtained after rake synthesis by the first synthesis unit (12), "24A" indicates the total amplitude Σ | R i ξ i ^ *| of the received symbol vector obtained after rake synthesis by the synthesis unit (24), and "25A" indicates the total amplitude Σ | ξ i ^ *| of the estimated channel value obtained by the synthesis unit (25). Value B is preset as a value less than total amplitude Σ | ξ i ^ *| of the estimated channel value, and used as a reference value by the comparator (32a). The level comparator (32a) compares total amplitude Σ | R i ξ i ^ * | of the received symbol vector, total amplitude Σ | ξ i ^ * | of the estimated channel value, and preset value B to determine the order of collation. Then the level comparator outputs the result of comparison . When the result of comparison by the level comparator (32a) is as follows, the selector (35) selects the signal output from the zero output device (33) and outputs it: B > Σ | R i ξ i ^ * | When the result of comparison by the level comparator (32a) is anything else, the selector selects the signal output from the hard-soft decision unit (31b) and outputs it. When the result of comparison by the level comparator (32a) is as follows, the hard-soft decision unit (31a) executes hard decision as described before: Σ | ξ i ^ | ≤ Σ | R i ξ i ^ * | When the result of comparison by the level comparator (32a) is as follows, the hard-soft decision unit (31a) executes soft decision: Σ | ξ i ^ | > Σ | R i ξ i ^ *| > B The following explains detailed operations of hard and soft decision in the embodiment shown in Figure 10. Figure 11 shows an example of the signal space where the decision unit (13) executes decision for the received signal to which QPSK modulation is applied. Assume that the result of comparison by the level comparator in the decision unit (13) is as follows (e.g., vector d in the figure): Σ | ξ i ^ | ≤ Σ | R i ξ i ^ *| In this case, estimated information symbol vector Z1^ (whose phase and amplitude is compensated to be normal) is output as the output signal for tentative decision from the selector (35). Here, "Z1^" is equivalent to "Zs^". Next, assume that the result of comparison by the level comparator in the decision unit (13) is as follows (e.g., vector e in the figure): Σ | ξ i ^ | > Σ | R i ξ i ^ * | > B In this case, the phase of the signal is compensated while its amplitude is maintained (by soft decision) because the signal is low in level and reliability. The decision result is output as an output signal for tentative decision from the selector (35). Next, assume that the result of comparison by the level comparator in the decision unit (13) is as follows (e.g., vector f in the figure): B > Σ | R i ξ i ^ * | In this case, the hard-soft decision unit does not execute decision. Then the zero output device (33) outputs zero as the output signal for tentative decision via the selector (35). If the total amplitude of received symbol vector Σ R i ξ i ^ * obtained after the rake synthesis is less than preset value B, zero is output as the estimated information vector because the reliability of the signal is very low. Thus, decision error can be reduced and the cancellation characteristic can be improved. Figure 12 shows yet another embodiment of the decision unit (13) shown in Figure 5. In Figure 12, "31c" indicates a hard-soft decision unit, "32c a level comparator, and "34" a phase comparator. Also, "12A" indicates received symbol vector Σ R i ξ i ^ * obtained after rake synthesis by the first synthesis unit (12), "24A" indicates the total amplitude Σ | R i ξ i ^ *| of the received symbol vector obtained after rake synthesis by the synthesis unit (24), and "25A" indicates the total amplitude Σ | ξ i ^ * | of the estimated channel value obtained by the synthesis unit (25). Value  A is preset as a value less than π/4, and used as a reference value by the phase comparator (34). Value  A is preset in a range where the phase difference from the normal phase in each quadrant can be properly maintained. The phase comparator receives input of total amplitude Σ | R i ξ i ^ *| of the received symbol vector and hard decision output from the hard-soft decision unit (13). The phase comparator calculates the phase difference  between both input signals and compares phase difference  with preset value  A to determine the order of collation. The phase comparator then outputs the result of comparison. Assume that the results of comparison by the level comparator (32c) and phase comparator (34) are as follows: Σ | ξ i ^ | ≤ Σ | R i ξ i ^ * |  <  A In this case (e.g., vector g in the figure), high reliability is determined. Then the estimated information symbol vector (which is the result of hard decision) is output as the output signal for tentative decision as described before. Next, assume that the results of comparison by the level comparator (32c) and phase comparator (34) are as follows: Σ | ξ i ^ | > Σ | R i ξ i ^ * |  <  A In this case (e.g., vector h in the figure), the result of soft decision (only the phase is compensated) is output as the output signal for tentative decision as described before. Next, assume that the result of comparison by the phase comparator (34) is as follows regardless of the result of comparison by the level comparator (32c):  >  A In this case (e.g., vector k in the figure), low reliability is determined. Then estimated information symbol vector Z2^ is output as the output signal for tentative decision with an amplitude less than the total amplitude of estimated channel value Z1^. Even if the total amplitude Σ | R i ξ i ^ * | of the received symbol vector is larger than the total amplitude Σ | ξ i ^ * | of the estimated channel value, low reliability is determined in specific cases. Low reliability is determined when phase difference  between estimated information symbol vector Z1^ (as the result of hard decision) and received symbol vector Σ R i ξ i ^ * exceeds preset value  A . This is because these vectors have phases close to adjacent quadrants. In such a case, the level of the signal can be changed to less than the total amplitude of the estimated channel value to suppress decision error caused by a large phase difference within a quadrant. Thus, the cancellation characteristic can be improved. Applications of this invention are not limited to previously described formats of implementation, but can be modified for various purposes. Different formats of implementation can also be combined. For instance, preset values A and B can be combined as follows. When the total amplitude of the received symbol vector exceeds the level specified by preset value A, the amplitude is changed to a lower level and soft decision is executed. When the total amplitude of the received symbol vector does not exceed the level specified by preset value B, zero is output. In addition, the decision unit (13) can be easily created in software by using a digital signal processor or field programmable gate array. The same procedure-can also be easily created using a circuit. As described above, the interference canceller compares the total amplitudes of the received symbol vector and estimated channel value, and compares preset values A and B. The reliability of the received symbol vector is judged through comparison. When high reliability is determined, hard decision is executed. When low reliability is determined, soft decision is executed with or without the level being lowered. Thus, decision error can be reduced and the accuracy of interference replica signal dm and estimated interference residual signal Sm output from each interference canceller unit can be increased. By increasing accuracy, the interference removal characteristics of the interference canceller can be improved.

Claims: A multistage interference canceller for cancelling interference in a communication system from an input signal, the interference canceller comprising: a plurality of despreading units (1) inputted with an error signal and an interference replica signal to produce received symbol vector and an estimated channel value; a synthesis unit (2) to synthesize said received symbol vector, an amplitude of the received symbol vector and an amplitude of the estimated channel value from each despreading unit (1), respectively; a decision unit (3,13) to evaluate said received symbol vector and output an information symbol vector; and a plurality of spreading units (4) inputted with said information symbol vector and said interference replica signal to produce an interference residual signal and a new interference replica signal outputted to the next stage of the interference canceller, Characterised in that the decision unit (3,13) comprises a hard-soft decision unit (9) which evaluates said received symbol vector by hard-soft decision according to a result of comparing the total amplitude of the received symbol vector and the total estimated channel value , and outputs the information symbol vector. The interference canceller according to claim 1, characterised in that each despreading unit includes a channel estimation unit (7) and said decision unit (3,13) includes a comparator (8) which compares the total amplitude of the received symbol vector output from said synthesis unit (2) with the total amplitude of the estimated channel value output from said channel estimation unit (7), and the hard-soft decision unit (9) executes a hard decision when the total amplitude of the received symbol vector is equal to or greater than that of the estimated channel value as a result of comparison by the comparator (8), or executes a soft decision when the result of comparison is otherwise. The interference canceller according to claim 1, characterized in that each despreading unit includes a channel estimation unit (7) and said decision unit (3,13) includes a comparator (8) which compares the total amplitude of the received symbol vector output from said synthesis unit, the total amplitude of the estimated channel value output from said channel estimation unit, and a preset value input into said comparator, the preset value being larger than the total amplitude of the estimated channel values, and in that the hard-soft decision unit changes the total amplitude of the received symbol vector to less than the total amplitude of the estimated channel value and executes a soft decision when the total amplitude of the received symbol vector is judged to be equal to or greater than the preset value, executes a hard decision when the total amplitude of the received symbol vector is judged to be less than the preset value and equal to or greater than the total amplitude of the estimated channel value, or executes a soft decision when the total amplitude of the received symbol vector is judged to be less than the total amplitude of the estimated channel values. The interference canceller according to claim 1, characterized in that each despreading unit includes a channel estimation unit and said decision unit includes a comparator which compares the total amplitude of the received symbol vector output from said synthesis unit, the total amplitude of the estimated channel value output from said channel estimation unit, and a preset value input into said comparator the preset value being less than the total amplitude of the estimated channel value, and a zero output device which outputs zero as a decision result, and in that the hard-soft decision unit outputs zero as a decision result from the zero output device when the total amplitude of the received symbol vector is judged to be less than the preset value by the comparator, executes a hard decision when the received symbol vector is judged to be equal to or greater than the total amplitude of the estimated channel value, or executes a soft decision when the received symbol vector is judged to be less than the total amplitude of the estimated channel value and equal to or greater than the preset value. The interference canceller according to claim 1, characterized in that each despreading unit includes a channel estimation unit and said decision unit includes a level comparator which compares the total amplitude of the received symbol vector output from said synthesis unit with the total amplitude of the estimated channel value output from said channel estimation unit, and a phase comparator which compares a phase difference between a result of a hard decision of the received symbol vector and said: received symbol vector with a preset phase value input into said comparator, and in that the hard-soft decision unit changes the level of the received symbol vector to a value less than the total amplitude of the estimated channel value, and executes a soft decision when the phase difference is judged to be equal to or greater than the preset value by the phase comparator, executes ahard decision when the phase difference is judged to be less than the preset value by the phase comparator, or the total amplitude of the received symbol vector is judged to be equal to or greater than the total amplitude of the estimated channel value by the level comparator, or executes a soft decision when the total amplitude of the received symbol vector is judged to be less than the total amplitude of the estimated channel value by the level comparator. A method of tentative decision in an interference canceller which includes an interference canceller unit, including a despreading unit (1), a despreader (6), a channel estimation unit (7), a first synthesis unit (2), a decision unit (3,13), a spreading unit (4), a spreader (10) and a second synthesis unit (5), including the steps of: inputting received signals, or error and interference replica signals from a previous stage, to the despreading unit (1); estimating a channel value in the channel estimation unit (7); synthesising a signal output from the despreading unit in the first synthesis unit (2); evaluating a signal output from the first synthesis unit (2) in the decision unit (3,13); inputting a decision output signal from said decision unit (3,13) and the estimated channel value to the spreading unit (4), and applying a signal output from the spreading unit to the second synthesis unit (5), the output of which is an estimated interference residual signal, characterized by the steps of; comparing in said decision unit (3,13) the total amplitude of a received symbol vector output from the first synthesis unit (2), with the total amplitude of the estimated channel value output from the channel estimation unit (7), and switching the decision operations executed in the decision unit (3,13), a hard decision being executed when the total amplitude of the received symbol vector output from the first synthesis unit is equal to or greater than the total amplitude of the estimated channel value, and a soft decision being executed when the total amplitude of the received symbol vector output from the first synthesis unit is less than the total amplitude of the estimated channel value. A method as claimed in claim 6, characterized in that in said comparing step the total amplitude of the received symbol vector output from the first synthesis unit, the total amplitude of the estimated channel value output from the channel estimation unit, and a preset value larger than the total amplitude of the estimated channel value are compared; and including the steps of: changing the total amplitude of the received symbol vector to less than the total amplitude of the estimated channel value and executing a said soft decision when the total amplitude of the received symbol vector is equal to or greater than the preset value; and executing a said hard decision when the total amplitude of the received symbol vector is less than the preset value and equal to or greater than the total amplitude of the estimated channel value, or executing a said soft decision when the total amplitude of the received symbol vector is less than the total amplitude of the estimated channel value. A method as claimed in claim 6, characterized in that in said comparing step the total amplitude of a received symbol vector output from the first synthesis unit, the total amplitude of the estimated channel value output from the channel estimation unit, and a preset value less than the total amplitude of the estimated channel value are compared; and including the steps of: outputting zero as a decision result when the total amplitude of the received symbol vector is less than the preset value; and executing a said hard decision when the received symbol vector is equal to or greater than the total amplitude of the estimated channel value, or executing a said soft decision when the total amplitude of the received symbol vector is less than that of the estimated channel value and equal to or greater than the preset value. A method as claimed in claim 6, characterized in that the comparing step further includes the step of comparing a phase difference between a result of a said hard decision of a received symbol vector and said relevant received symbol vector with a preset phase value; changing the level of the received symbol vector to a value less than the total amplitude of the estimated channel value, and executing a said soft decision when the phase difference is equal to or greater than the preset phase value, or executing the a said hard decision when the phase difference is less than the preset phase value and the total amplitude of the received symbol vector is equal to or greater than the total amplitude of the estimated channel value, or executing a said soft decision when the total amplitude of the received symbol vector is less than the total amplitude of the estimated channel value.

Inventors: KOBAYAKAWA SHUJI, SEKI HIROYUKI, TANAKA YOSHINORI, TODA TAKESHI, TSUTSUI MASAFUMI, KOBAYAKAWA, SHUJI, SEKI, HIROYUKI, TANAKA, YOSHINORI, TODA, TAKESHI, TSUTSUI, MASAFUMI
Applicants: FUJITSU LTD, FUJITSU LIMITED
Application year: 1997
Main classification: H04B1
IPC codes: H04B7, H04B1, H04J13