COLLISION WARNING SYSTEM

Abstract: A collision warning system (10) discriminates between objects which pose a threat of collision from those which do not by measuring the relative sightline rate of the object, this being a measure of the rate of change of angular position of the object if the sightline rate is above a threshold value, there is little risk of collision. To measure the sightline rate, a radar source (20) emits microwave frequency radiation which is received by two detectors (22 and 24) after reflection from a target. Signals from the detectors are processed by processing means (26). The processing means determines if the sightline rate of an object is below a certain threshold. If it is, and the relative velocities of the object and the system are such that a collision is likely, a warning buzzer (28) sounds.

Description: COLLISION WARNING SYSTEM The present invention relates to a system for providing a collision warning There is currently world-wide interest in the production of systems for providing a vehicle collision warning. Projected capabilities range from relatively simple "intelligent cruise control" systems, to more complex systems capable of searching the road ahead and alerting/acting on the presence of a potential hazard. For all weather performance, particularly in dense fog, a radar sensor is particularly beneficial Considerable problems must be overcome before a truly cost-effective radar based system can be produced Particularly important problems of implementation are: a. false alarms from vehicles in adjacent lanes and "road furniture" (street signs, lamp standards etc.); b. mutual interference between radar systems; c. reliably discnminating vehicles and structures which are a potential hazard from those which are not an immediate safety threat; and d. producing a cost-effective hardware configuration which will cope with the above problems. Several research organizations have been involved in developing collision warning radar systems. A.G. Stove of the Philips Research Laboratories in Electronics and Communication Engineenng Journal, October 1991 , pages 232-240 provides a review of the use of radar in vehicle collision warning systems. Such systems generally comprise a microwave transceiver for transmitting and receiving radar signals, a signal processor for identifying potential obstacles, and a form of man- machine interface such as a display for informing the driver of the vehicle The system generates a radar map of all the obstacles within the field of view of the transceiver and then extracts those obstacles which are a potential threat for display. In certain situations, such as rounding a bend, an obstacle rich environment in front of the vehicle may be measured although there is no real danger presented to the vehicle, provided it negotiates the bend. The signal processing capability required to cope with such an obstacle nch environment is considerable and adds to the complexity and expense of such systems. The vehicle component market is extremely price sensitive and the reduction of unit cost is of critical importance. European Patent Application No. 0 473 866 A2 describes an optical system in which the range and angle of target vehicles are monitored and these are passed to a processor which monitors each target vehicle and determines the predicted separation distance. Such a system would require a processor having a substantial data processing capacity to cope with monitoring each target vehicle even when the majority of the target vehicles do not present a collision hazard. It is known, for example in United Kingdom patent specification number 1 313 402 that the necessary and sufficient condition for the collision of a first moving body with a second stationary or moving body is that the relative separation of the bodies decreases with time whilst the relative bearing of the second body measured from the first body remains constant. United Kingdom patent specification number 1 605 171 describes an aircraft based system for determining the clearance of the aircraft from a landscape feature by determining the angle below the flight line of the aircraft of a sightline from the aircraft to the feature, the ground speed of the aircraft and the rate of increase of the angle of the sight line below the honzontal. The present invention provides a vehicle collision warning system compnsing: (i) a source of microwave radiation; (ii) receiving means for receiving radiation emitted by said source and reflected by an object in a field of view of said receiving means and for generating receiver signals in response thereto, said signals having a respective phase and frequency; and (iii) processing means for processing said signals to determine whether said object presents a collision nsk, characterized in that: (A) said receiving means comprises at least two laterally separated receivers, each for generating respective receiver signals, and (B) said processing means comprises means for determining from said receiver signals a measure of the sightline rate of said object and means for rejecting signals associated with objects having a sightline rate greater than a set value in order to distinguish between objects which present a collision risk and objects which do not present such a risk, said sightline rate being the rate of change of the angular position of an object with respect to the system. The present invention discriminates between objects which pose no threat of collision and objects with which collision is considered likely on the basis of a measurement of the rate of change of the angular position of the object with respect to the measuring system. This rate is known as the sightline rate. Objects with a low sightline rate are those which are at an angular position to the measuring system which is slowly changing with time. If the object is approaching the measuring system and the sightline rate is low, then collision is likely. Objects which exhibit a high sightline rate are unlikely to be a threat unless they are moving at a high relative speed or they are at close range. Whilst the invention is identified as a collision warning system, such systems need not provide a physical warning such as an audible or visual signal but may provide a warning to a control system which uses the warning to control the motion of for example a vehicle carrying the system, such as applying the brakes. The invention provides the advantage over prior art radar-based collision avoidance systems of not requiring processing means to determine the position and relative motion of all targets prior to determining which present a collision hazard. Only those targets which have a sightline rate below a threshold level are processed, thereby reducing the data processing requirement of the system. With at least two laterally separated receivers, the sightline rate of target objects may be determined. In the case of an automobile collision warning system, separating two receivers by the width of the automobile provides a suitable separation for angle determination. Such angular determination may be performed by analysing the phases of receiver signals, although other techniques might be employed. If the receiver signals from two laterally separated receivers are added together, the resultant composite signal has an interference fringe type characteristic with the sensitivity to received radiation having an angular distribution of sensitivity maxima separated by sensitivity minima. This characteristic may be used to obtain a measure of a target objects sightline rate. As the target object passes through angles corresponding to sensitivity minima, the signal to noise ration of the signals is low and the phase of the signals will be essentially random. The second differential with respect to time of the signal phase may be used to compare with a threshold value to determine whether a target object's sightline rate exceeds a set value. It may be shown that a miss distance Z for an object at a range R and a relative velocity V and a sightline rate ω s may be determined by the equation Z = ω s R 2 (1). V A collision warning system which discriminates objects according to their sightline rate where only those objects which pose a threat are detected and all other objects are rejected as early as possible provides the advantage that complex threat assessment processing is not required. ln situations where many objects are detected, prior art collision warning systems which determine a collision risk on the basis of an objects track history may overload, leading to false alarms or missed threats. Particular problems with track processing systems occur when the vehicle carrying the system enters a bend in the road. Furthermore, the need to discriminate between many objects in the field of view may lead to a requirement for high range resolution. Such systems may be very complex and hence expensive to implement. The collision warning system of the invention may incorporate means for controlling the frequency of the source such that it is orientation dependent. Such a system might provide benefits in avoiding confusion between systems of other vehicles. The receivers of the invention may be conventional horn-type receivers. Focal plane array systems might also be used, with angular sensitivity being enhanced by having antenna elements at the focal plane of the receiver which have respective look directions. In a further aspect, the invention provides a system for providing a collision warning, characterized in that the system includes means for distinguishing objects presenting a collision hazard from objects which do not present an immediate collision hazard by measurement of each object's sightline rate, the sightline rate being the rate of change of the angular position of the object with respect to the system. The system of the invention may be a road-vehicle collision warning system. The system may comprise a source of electromagnetic radiation and detectors for receiving the radiation after reflection from an object together with signal processing means for determining the sightline rate of objects. The system may operate at microwave frequencies with microwave detectors providing a sensitivity to received radiation which is angle dependent. A reduced frequency signal may be generated at the detectors which is then processed further. Typically, the system emits a frequency modulated continuous wave signal. The reduced frequency signals may be passed to a fast Fourier transform unit, the complex output of which includes a phase angle. By calculating a second time derivative of the phase angle, the sightline rate of detected objects may be compared with a threshold value. Objects having a sightline rate above the threshold value do not pose a risk of collision and may be rejected. Objects with a sightline rate below the threshold level may pose a collision risk, and so signals from these objects are processed further to determine whether they are within the safe braking distance of the system carrying vehicle. Microwave detectors in the form of focal plane receivers with a plurality of antenna elements provide a degree of angular sensitivity. A focal plane receiver may include non-radiative means for coupling a local oscillator signal to signal mixing means. In order to reduce interference from the collision warning systems of other vehicles, the frequency of transmitted radiation may be varied according to the direction of travel of the system carrying vehicle. A magnetic compass may be used to control a master oscillator so that for a particular range of magnetic bearings, a particular frequency is transmitted. In another aspect, the invention provides a vehicle collision warning system comprising a radiation source, means for receiving reflected radiation and for generating signals in response thereto and means for processing the signals to determine a collision risk, wherein the radiation source provides means for emitting radiation whose frequency is dependent upon an orientation of the system. In a further aspect of the invention, there is provided a receiver element for receiving microwave radiation, for mixing the received radiation with a local oscillator signal and for extracting an intermediate frequency signal, wherein the element comprises receiving means for receiving the radiation and coupling means for coupling the local oscillator signal to the receiving means and for extracting the intermediate frequency signal, the coupling means comprising conducting means for carrying the local oscillator signal from a source to the receiving means and for carrying the intermediate frequency signal from the receiving means and a plurality of diodes connecting the conducting means to the receiving means. In order that the invention may be more fully understood, embodiments thereof will now be described, by way of example only, with reference to the accompanying drawings, in which:- Figure 1 is a schematic diagram of a system of the invention; Figure 2 shows a receiver beam pattern of the Figure 1 system; Figure 3 is a series of graphs illustrating the operation of the Figure 1 system; Figure 4 is a schematic diagram of a further system of the invention, Figure 5a is a sectional view of a focal plane receiver of the Figure 4 system; Figure 5b shows a sectional view of a lens of the Figure 5a receiver; Figure 6 shows a plan view of antenna elements of the Figure 5a receiver; Figure 7a shows a plan view of an alternative antenna element of the Figure 5a receiver; Figure 7b shows a sectional view of the Figure 7a antenna element, and Figure 7c shows a more detailed plan view of the Figure 7a antenna element. Refemng to Figure 1 there is shown a collision warning radar system indicated generally by 10 which would be mounted on a vehicle. The system 10 includes a microwave transmit antenna 20, two microwave receive antennas 22 and 24, and a signal processor 26 connected to a warning buzzer 28. The microwave transmit antenna 20 is a conventional waveguide horn emitting microwave radiation having a frequency in the range 76 to 77 GHz. The transmit antenna 20 produces a radar beam which is 10° wide in azimuth. The radar beam is a transmitted signal which is a single sweep linear frequency modulated continuous wave (FMCW) signal, as descnbed by Stove in the previously referenced article. The FMCW signal is generated by a source 30 and passed to the transmit antenna 20 via a transmission line 32. The receive antennas 22 and 24 are separated laterally by a distance of 1.2 metres and are each a horn type antenna having an angle of sensitivity of 10° to match the beamwidth of the transmit antenna 20. The FMCW signal from the source 30 is passed to signal mixers 34 and 36 via respective transmission lines 50 and 52. Signals emitted by the transmit antenna 20 and received by the receive antennas 22 and 24 after reflection from an object are mixed by the mixers 34 and 36 with the original FMCW signal from the source 30 to produce respective video-frequency outputs. The outputs pass to respective amplifiers 58 and 60. The resulting outputs from the two amplifiers are added together produce an output A and subtracted one from the other to produce an output B. Output A is produced by a summing amplifier 62 which adds the outputs of the amplifiers 58 and 60 directly. The outputs of the amplifiers 58 and 60 are also passed to an operational amplifier 66 which generates an output signal proportional to the difference between its two inputs. The operational amplifier 66 generates the output B The analogue signals of outputs A and B are each digitised by a respective one of two analogue to digital converters 70 and 72 and thence processed in a respective one of two Fast Fourier Transform (FFT) units 74 and 76 to extract object range information from the outputs as in a conventional FMCW radar system. The system 10 is constructed so as to have a maximum range of 200 metres. This 200 metre operating range is divided into eight 25 m range gates. The FFT units 74 and 76 each process the digitised input signals. Each FFT unit 74 and 76 has eight outputs, corresponding to the eight range gates. For ease of illustration, only one output is shown from each FFT unit in Figure 1. If an object is present in a particular range gate, each of the FFT units generates a complex number output signal on the output corresponding to that range gate. The amplitude of the output signal provides an indication of the object's size and the phase angle of the signal is a function of the object's range from the radar system. The eight outputs of each FFT unit 74 and 76 are connected to a respective coherence detection unit. In Figure 1 , for ease of illustration, only a single output 78 from the FFT unit 74 and a single output 79 from the FFT unit 76 are shown connected to respective coherence detection units 80 and 82. The radar system 10 has seven other coherence detection units connected to each FFT unit which are not shown. The coherence detection units 80 and 82 compare the phase angles of successive output signals of the FFT units 74 and 76 and reject signals from objects which do not pose a risk of collision as will be described later. Coherence detectors have been described by G.C.Goddard in a paper in the Proceedings of the IEE Colloquium on Adaptive Thresholding, London, England, 25 March 1981 , pages 9.1 to 9.6. Signals which are not rejected by the coherence detection units and which therefore indicate objects of significant collision risk are passed to a signal processor 90. The signal processor 90 compares the range of these objects with the speed of the automobile carrying the radar system 10. If the object is within a distance equal to the stopping distance of the automobile plus the distance which would be travelled in a two second warning period, the warning buzzer 28 is activated. Referring to Figure 2 there are shown receiver beam patterns for the outputs A and B. A dotted line 152 indicates the receiver beam pattern of output A and a solid line 154 indicates the receiver beam pattern of output B. The receiver beam pattems indicate the sensitivity to objects of the outputs as a function of angle. The receiver pattems comprise a series of lobes, such as a lobe 156 separated by nulls such as a null 158. The nulls occur at angles θ n , where for small angles away from a central direction as required for a collision warning radar: nλ for channel A θ n + φ = — n = 0, 1, 2, 3 . . . . (2) for channel B θ a + φ = (w + -)- n = 0, 1 , 2, 3 . . . . (3) where λ is the wavelength corresponding to the operating frequency; L is the spacing between the receive antennas 22 and 24; and φ is an arbitrary offset angle determined by the relative phasing of the receive antennas 22 and 24. Objects with low sightline rates will remain within a single lobe of the composite antenna patterns of Figure 2 between successive measurements. Objects with more than a certain minimum sightline rate will pass through at least one null on either channel A or B between successive measurements. The two channels A and B are necessary in order to ensure the detection of objects with low sightline rates at angles which correspond to nulls in either of the channels. The relative phase between the local oscillator signals to the two receivers may be quite arbitrary, with the antenna pattern of Figure 2 being shifted as a whole relative to an antenna assembly boresight. Referring now to Figure 3, the operation of the coherence detection units 80 and 82 of Figure 1 will now be described. Objects having a low sightline rate and a high signal to noise ratio have a phase history in which the phase of the received signal changes linearly with time. The phase history of noise is totally random. If an object has sufficient sightline rate to pass through one or more nulls in the receive antenna pattern, where the signal to noise ratio is low, the phase history will have regions where it becomes random. Figure 3(a) shows a graph of the phase angle of a signal from an object with a low sight line rate against time. The phase history of this object is essentially linear. Figure 3(b) shows a graph of the phase angle against time of a signal from an object with a sightline rate sufficient to have passed through two nulls in the receiver antenna pattern. The phase history shown in Figure 3(b) has two regions 170 and 172 where the phase history is random, corresponding to the times where the object was at angles relative to the radar system corresponding to receiver antenna nulls. Figure 3(c) shows the phase history of noise alone, where the phase history is random throughout the processing interval. Figures 3(b) and 3(c) represent the phase histories measured during processing intervals where objects presenting a hazard were not detected. In order to distinguish phase histories such as that shown in Figure 3(a) from phase histories such as those shown in Figure 3(b) and Figure 3(c) which may be rejected, the phase history is differentiated twice with respect to time to obtain a measurement referred to here as the second angular difference. The magnitudes of variations in the second angular difference are compared with a predetermined threshold. Figure 3(d) shows a graph of the second angular difference against time for the measurements shown in Figure 3(a). The predetermined threshold is represented by a dashed line 174. Since the phase history in this instance is substantially linear, the second angular difference is always close to zero and does not cross the line 174. The second angular differences of the cases shown in Figures 3(b) and 3(c) produce crossings of the threshold, as shown in Figures 3(e) and 3(f) respectively One cntenon for distinguishing objects which pose a threat from other objects is whether the object passes through no more than one third of the angular distance between nulls in the patterns of Figure 2 during a coherence detector processing interval T p . Under these conditions, an object return should be detected in at least one of the channels A or B. This sets an upper limit on the sightline rate such that: . (4). 3LT Combining equations (1) and (4), the following limit on the coherence detector processing interval is obtained: λR 2 T < -^— (5). ' 3LZV Each of the FFT outputs corresponds to a particular range R. For a given range and closing velocity, equation (5) enables a minimum hazard miss distance to be specified by varying the coherence detector processing time for the FFT output which corresponds to that range. In practice, however, the coupling between range information and Doppler shifting inherent in FMCW radar operation results in a distortion of the apparent range of an object. A further consequence of this coupling is that a single sweep FMCW radar will give incorrect information on the relative velocity of potential hazards. In practice, these errors will usually be small. In an alternative embodiment, the single sweep FMCW signal may be replaced by a FMCW signal which has both an upsweep and a downsweep. Such signals enable separate range and relative velocity information to be obtained. A system incorporating upsweep and downsweep FMCW would require signal processing modified from that of the system 10 to separate the range and velocity information pπor to coherence detection. Often radar transmitters and receivers have a beam pattern which comprises a main beam flanked by one or more sidelobes. Sidelobes are unsatisfactory in a collision warning radar system since it would not be possible to distinguish objects which present a hazard from objects which although they are close are not an immediate safety threat. For example, a vehicle which is immediately on the offside or nearside of the radar carrying vehicle could present an object with apparently no relative velocity and very close range if it were in the radar sidelobes, and would be indistinguishable from a close range object in front of the radar carrying vehicle. The object would appear to intrude within the safe braking distance and would cause an alarm. Radar antenna sidelobes may be reduced by placing the antenna assembly at one end of a tube of radiation absorbing material. Although this would narrow the field of view unacceptably for most radar applications, the required field of view for a collision warning radar is relatively small and so this represents a cost effective method of reducing sidelobes. Once a substantial percentage of the number of vehicles on the road are fitted with collision warning radar systems, interference may be caused between radar systems operating in the same area. Varying the ramp rate of the FMCW signal between systems might provide some protection to this problem. A further method of providing protection against mutual interference is to link a radar system's transmit frequency to the direction of travel of the system carrying vehicle. The European frequency allocation for collision warning radar systems is 76 to 77 GHz. This may be subdivided into ten 100 MHz wide channels which are each allocated to a particular 36° wide sector of azimuth angles. Two vehicles which approach head-on would then have a respective radar operating frequency separated from the operating frequency of the other vehicle by 500 MHz. After periodic time intervals a control circuit measures an output signal from either an electronic or mechanical compass. A control signal is then sent to a radar master oscillator to control the operating frequency of the oscillator and hence the transmitted frequency. The radar system 10 incorporates hom type receive antennas 22 and 24. In place of horn type receive antennas, focal plane receivers may be advantageously incorporated into the design of a collision warning radar system. Focal plane receivers are described in UK Patent No. 2279179. Figure 4 shows a schematic diagram of a radar system of the invention, indicated generally by 200, incorporating focal plane receivers 202 and 204 The radar system 200 is similar to the radar system 10 of Figure 1 except that the focal plane receivers 202 and 204 each have three receive antenna elements 206a to 206c and 208a to 208c respectively Each receive antenna element has its own respective output and so switching units 210 and 212 are required to selectively connect the signal processing components to each output in turn In the system 200, a FMCW source 220 generates a single sweep FMCW signal which is passed to a conventional waveguide horn type transmit antenna 224 which generates a radar beam which is approximately 10° wide in azimuth and with a sufficiently wide elevation beamwidth to match the field of view of the receivers 202 and 204 The signal from the FMCW source 220 is passed to each of the receivers 202 and 204 Signals received by the antenna elements 206a to 206c and 208a to 208c after transmission from the transmit antenna 224 and reflection off an object are mixed with the signal from the FMCW source 220 to generate a video-frequency output Apart from the multiplexing of the receiver output by the switching units 210 and 212, the signal processing for the system 200 is the same as that for the system 10 and will not be descnbed further The receivers 202 and 204 are identical Referring now to Figure 5a there is shown a horizontal section of a focal plane receiver, indicated generally by 250 The receivers 202 and 204 are like to the receiver 250 The receiver 250 compnses a lens 252 having a focal plane 254 The lens 252 has a front portion 256, which is an ellipsoidal segment having a maximum diameter of 75 mm, and a rear portion 258 which is frusto-conical in shape The lens 252 is of a titanium dioxide loaded polystyrene dielectnc, a matenal manufactured by Plessey Semiconductors of Lincoln, England, having a dielectπc constant ε r of 10 The lens 252 incorporates a metal gπd 260 sandwiched between the front portion 256 and the rear portion 258 The grid 260 is in the form of a planar array of linear conductors seen end-on in the drawing, which in operation are arranged vertically An alumina substrate 262 is attached to a rear surface 263 of the rear portion 258. The substrate 262 has an outer surface 264 in the focal plane 254. Three antenna elements 270a, 270b, and 270c, collectively referred to as the antenna elements 270, are located on the surface 264 of the substrate 262 at the focal plane 254 to provide sensitivity to radiation from three respective look angles. The antenna elements 270 are each a crossed dipole antenna. A central antenna 270b receives radiation arriving parallel to an axis 272 and side antennas 270a and 270c receive radiation from +3° and -3° to the axis 272 respectively. The antenna elements 270 are centred on a single horizontal axis of the focal plane 254, spaced apart by a centre to centre spacing of 1.15 mm. Each dipole is of length 0.85 mm, as appropriate for resonance in a frequency range which includes the frequency range 76 to 77 GHz at an interface between air and the substrate 262. A microwave feed waveguide 280 connected to the FMCW source 220 (not shown) has an open output end 282 close to the substrate 262. Microwave input power from the FMCW source 220 is fed along the waveguide 280; it is polarised vertically in the plane of the drawing, as indicated by an encircled cross 284 The waveguide provides a local oscillator signal (LO) for the antenna elements 270. Each of the antenna elements 270 is a crossed dipole antenna having two mutually orthogonal planar dipoles comprising a pair of dipole limbs. One of the dipoles of each antenna element is arranged vertically in the plane of the drawing, parallel to the conductors of the metal grid 260, the other dipole is arranged hoπzontally . Radiation which is transmitted by the transmit antenna 224 and reflected off an object may be received by the receiver 250. The grid 260 acts as a polariser, only allowing hoπzontally polarised radiation to reach the antenna elements 270 as a receive signal RX. Figure 5b shows a cross-sectional view of the lens 252. The front portion 256 is hypohemi-ellipsoidal in shape, i.e. a fraction of a hemi-ellipsoid, having a major axis 290 of length 82.7 mm and a minor axis 292 of length 78.3 mm. The frusto-conical rear portion 258 has a curved surface such that in cross-section it subtends an angle of 50° to a line parallel to the major axis. The rear surface 263 is circular and has a diameter of 28 mm. The lens 252 has an overall thickness, r, of 55 mm. Referring to Figure 6 also there is shown a plan view of the antenna elements 270a, 270b, and 270c. The antenna elements 270 each comprise two dipoles 302 and 304. The dipoles 302 each comprise two limbs 306 and 308 and dipoles 304 each comprise two limbs 310 and 312. The limbs 306 to 312 are each 0.325 mm in length and 0.14 mm in width. The limbs 312 are each longitudinally divided having two arms 312a and 312b separated by a gap 313, 0.04 mm in width. The antenna elements 270 each have a ring of four radar frequency mixer diodes 314a to 314d connected between respective dipole limbs of different dipoles. The limbs 306 and 308 are connected to the anodes of diode pairs 314a/314b and 314c 314d respectively and the limbs 310 and 312 are connected to the cathodes of diode pairs 314b/314c and 314a/314d respectively. The diodes 314a to 314d are consequently polarised towards the limbs of one dipole and away from the limbs of the other. The arms 312a and 312b of the split limb 312 are connected to respective diodes 314a and 314d. The dipoles of the antenna elements 270 which incorporate the split limbs are arranged to be parallel to the polarization of the local oscillator signal. The other dipoles are arranged to be parallel to the polarization of radiation transmitted by the The LO and RX signals couple to the dipoles to which their polarizations are parallel. The LO and RX signals are mixed by the diodes 314a to 314d to produce intermediate frequency (IF) signals. The IF signals are at the difference frequency between the LO and RX signals. The split limb appears as a single limb at radar frequencies by virtue of capacitive coupling between the limbs. At the intermediate frequency however, it acts as two parallel conductors forming a transmission line. The split limb consequently provides an output feed for relaying the IF signals to the processing circuitry. The processing is carried out in a manner previously described in relation to the radar system 10. Whereas the radar system 10 had eight coherence detectors for each output of the FFT units, the processing circuitry of the system 200 requires three banks of eight coherence detectors for each FFT unit, together with a multiplexing unit for switching the outputs of the FFT unit to an appropriate bank in co-ordination with the switching units 210 or 212 as appropriate. Provided suitable data processing capability is provided in the coherence detectors, the multiplexing unit may be dispensed with; the data processing would need to incorporate a means of processing data from each look direction in a time multiplexed manner. If the cost of added electrical circuitry is not a major concem, the switching units 210 and 212 may be dispensed with and in their place three separate sets of processing circuitry provided - one for each look direction of the receivers 202 and 204. In place of the feed waveguide 280 providing a LO signal, the LO signal might be fed directly to the receive antennas. A focal plane receiver incorporating such an arrangement would be similar to the receivers 202 and 204 without the waveguide 280. Referring to Figure 7a, there is shown a plan view of an alternative antenna element 350 for incoφoration in such a receiver. Referring to Figure 7b also, there is shown a cross section of the antenna element 350 along a line VII-VII in Figure 7a. The antenna element 350 is mounted on a first side of an alumina substrate 351 and comprises a dipole 352 having two limbs 354a and 354b and a LO signal feed structure 356. The dipole 352 has a width of 0.14 mm and an overall length of 0.85 mm, with each limb 354a and 354b being 0.405 mm in length. The feed structure 356 comprises a first conductor 358 on the first side of the substrate and a second conductor 360 on a second side of the substrate. The first conductor 358 has a constant width of 0.2 mm, whereas the second conductor 360 has a width which varies along its length. Along a central region 361a, the second conductor 360 has a width of 0.3 mm, at an end region 361b it has a width of 0.2 mm, and in a third region 361c the width extends from 0.3 mm to width of approximately 3 mm. The second conductor 360 acts as a ground plane and is connected to earth. Figure 7c shows a more detailed plan view of a section of the antenna element 350. The first conductor 358 is connected to the two limbs 354a and 354b by two diodes 362a and 362b. The second conductor 360 is connected to the limbs 354a and 354b via a plated through-hole 364 through the substrate 351 and connecting lines 366a and 366b respectively. The connecting lines 366a and 366b are each 0.42 mm in length and 0.08 mm in width and are separated by a gap 0.04 mm in width. A LO feed signal is coupled to the first conductor 358. Radiation received by the antenna element 350 after reflection from a remote object is mixed with the LO signal, producing an IF signal which is extracted via the first conductor 358. Whilst the antenna elements 270 and 350 have been designed so as to operate in the frequency range 76 to 77 GHz, a person skilled in the art of microwave antenna design will appreciate that for operation at other frequencies the dimensions of the components of the antenna elements would have to be modified as appropriate for operation at the desired frequency. Each dipole has an effective length which is its physical length multiplied by the square root of the average of the dielectric constants of the two media on either side of it. For example the dipole 352 has air on one side (ε = 1) and alumina (ε = 10) on the other, and so its effective length is 0.85 mm multiplied by ^ (10 + 1) . This is 2.0 mm which is a half wavelength in free-space of microwave radiation of approximately 75 GHz. If desired, the length of the dipoles may be altered so that they have an effective length of nλ/2 where λ is the free-space wavelength and n is an odd integer. If n were to be greater than 1 , the centre to centre spacing of the dipoles would need to be increased, and such an arrangement might not be as efficient. In alternative embodiments, the systems 10 and 200 described with reference to Figure 1 and 4 respectively may be modified such that the FMCW source generates a FMCW signal which has a frequency which is a sub-multiple of the output frequency. For example, the FMCW source may generate a signal which has a frequency one quarter of the output frequency. A frequency multiplier, and advantageously an amplifier, is then required between the FMCW source and the transmitter. In the above example, a four-times frequency multiplier would be required. The signal mixers, such as the mixers 34 and 36 and the antenna elements 270 are arranged to operate on harmonics of the FMCW source frequency; there is no requirement for frequency multipliers between the FMCW source and the mixers.

Claims: CLAIMS 1. A vehicle collision warning system comprising: (i) a source of microwave radiation; (ii) receiving means for receiving radiation emitted by said source and reflected by an object in a field of view of said receiving means and for generating receiver signals in response thereto, said signals having a respective phase and frequency; and (iii) processing means for processing said signals to determine whether said object presents a collision risk, characterized in that: (A) said receiving means comprises at least two laterally separated receivers, each for generating respective receiver signals, and (B) said processing means comprises means for determining from said receiver signals a measure of the sightline rate of said object and means for rejecting signals associated with objects having a sightline rate greater than a set value in order to distinguish between objects which present a collision risk and objects which do not present such a risk, said sightline rate being the rate of change of the angular position of an object with respect to the system. 2. A system according to Claim 1 , characterized in that said processing means includes phase analyzing means for analyzing the phase of said receiver signals and for rejecting signals having a phase history over a processing interval indicative of a sightline rate greater than said set value. 3. A system according to Claim 2, characterized in that said processing means includes combining means for combining signals from a plurality of said at least two receivers to generate composite signals at respective composite signal outputs, each composite signal output having an associated composite antenna pattern of sensitivity to received radiation comprising a series of sensitivity maxima separated by sensitivity minima 4. A system according to Claim 3, characterized in that said receiving means comprises two receivers and wherein said combining means comprises means for adding receiver signals from said receivers to form a first composite signal at a first composite signal output and for subtracting one receiver signal from the other to form a second composite signal at a second composite signal output and wherein the sensitivity maxima of the first composite output's composite antenna pattern are at angles which correspond to angles of sensitivity minima of the second composite output's composite antenna pattern. 5. A system according to Claim 4, characterized in that said phase analyzing means comprises digitizing means for digitizing the first and second composite output signals and means for performing a Fast Fourier Transform (FFT) thereon and outputting transformed signals to a plurality of FFT outputs and a respective coherence detection unit connected to each FFT output for comparing the phase angles of successively output transformed signals. 6. A system according to Claim 5, characterized in that each coherence unit provides means for generating the second differential with respect to time of the phase of the transformed signals for comparison with a threshold value. 7. A system according to Claim 5 or 6, characterized in that each coherence detection unit has a processing interval dependent on the FFT output to which it is connected. 8. A system according to any preceding claim, characterized in that the at least one receiver is a horn type antenna. 9. A system according to any one of Claims 1 to 7, characterized in that said at least one receiver is a focal plane array receiver. 10. A system according to any preceding claim, characterized in that said source emits radiation having a frequency which is dependent upon an orientation of the system. 11. A system for providing a collision warning, characterized in that the system includes means for distinguishing objects presenting a collision hazard from objects which do not present an immediate collision hazard by measurement of each object's sightline rate, the sightline rate being the rate of change of the angular position of the object with respect to the system. 12. A system according to Claim 11, characterized in that the system is a road- vehicle collision warning system. 13. A system according to Claim 12, characterized in that the system comprises at least one source of electromagnetic radiation, receiving means for detecting the radiation after reflection from an object and for generating signals in response thereto, and signal processing means for determining the sightline rate of an object from the signals. 14. A system according to Claim 13, characterized in that the at least one source of radiation is a microwave source and the receiving means comprises a plurality of microwave detectors linked so as to provide detection means having a sensitivity to received radiation which is incident angle dependent. 15. A system according to Claim 14, characterized in that the detection means is arranged to mix a local oscillator signal with the reflected signals in order to generate signals of reduced frequency for further processing. 16. A system according to Claim 15, characterized in that the processing means comprises at least one means for performing a fast Fourier transform (FFT) on the reduced frequency signals and coherence detection means for comparing the second time differential of a phase angle generated by the FFT with a threshold value. 17. A system according to Claim 16, characterized in that the plurality of microwave detectors comprises a first and a second microwave detector and the processing means further comprises means for adding reduced frequency signals from each of the microwave detectors in phase and means for adding the reduced frequency signals in anti-phase. 18. A system according to any one of Claims 14 to 17, characterized in that the microwave detectors are focal plane detectors comprising a plurality of antenna elements. 19. A system according to Claim 18, characterized in that the focal plane detectors include non-radiative coupling means for coupling a local oscillator signal to signal mixing means. 20. A system according to any one of Claims 14 to 19, characterized in that the radiation source is arranged to emit radiation whose frequency is dependent upon an orientation of the system. 21. A vehicle collision waming system comprising a radiation source, means for receiving reflected radiation and for generating signals in response thereto and means for processing the signals to determine a collision risk, characterized in that the radiation source provides means for emitting radiation whose frequency is dependent upon an orientation of the system. 22. A receiver element for receiving microwave radiation, for mixing the received radiation with a local oscillator signal and for extracting an intermediate frequency signal, characterized in that the element comprises receiving means for receiving the radiation and coupling means for coupling the local oscillator signal to the receiving means and for extracting the intermediate frequency signal, the coupling means comprising conducting means for carrying the local oscillator signal from a source to the receiving means and for carrying the intermediate frequency signal from the receiving means and a plurality of diodes connecting the conducting means to the receiving means. 23. A receiver element according to Claim 22 characterized in that the element is mounted on a dielectric substrate. 24. A receiver element according to Claim 23, characterized in that the conducting means comprises a plurality of conducting strips arranged on respective sides of the substrate. 25. A receiver element according to Claim 23, characterized in that the receiving means is disposed at the focal plane of a microwave lens.

Inventors: DEAN MICHAEL, HODGES ROBERT DAVID, DEAN, MICHAEL, HODGES, ROBERT, DAVID
Applicants: DEAN MICHAEL, HODGES ROBERT DAVID, SECR DEFENCE, DEAN, MICHAEL, HODGES, ROBERT, DAVID, THE SECRETARY OF STATE FOR DEFENCE
Application year: 1997
Main classification: G01S13
IPC codes: G01S7, G01S13