Algebraic codebook with signal-selected pulse amplitudes for fast coding of speech

Abstract: The present invention relates to a method and device for conducting a search in a codebook. This codebook consists of a set of pulse amplitude/position combinations each defining a number L of positions p and comprising both zero-amplitude pulses and non-zero-amplitude pulses assigned to respective positions p = 1, 2, ...L of the combination. Also, each non-zero-amplitude pulse assumes one of q possible amplitudes. According to the method, a subset of combinations is pre-selected from the codebook, and the search is limited to this subset to reduce complexity thereof. To pre-select the subset, an amplitude/position function is pre-established in relation to the sound signal. Pre-establishing the amplitude/position function includes pre-assigning one of the q possible amplitudes to each position p by (i) processing the sound signal to produce a backward-filtered target signal D and a pitch-removed residual signal R', (ii) calculating an amplitude estimate vector B in response to the signals D and R', and (iii) for each position p, quantizing an amplitude estimate B p of the vector B to obtain the amplitude to be selected for that particular position p.

Description: BACKGROUND OF THE INVENTION 1. Field of the invention: The present invention relates to an improved technique for digitally encoding a sound signal, in particular but not exclusively a speech signal, in view of transmitting and synthesizing this sound signal. 2. Brief description of the prior art: The demand for efficient digital speech encoding techniques with a good subjective quality/bit rate trade-off is increasing for numerous applications such as voice transmission over satellites, land mobile, digital radio or packed network, voice storage, voice response and wireless telephony. See document WO 91/13432 A. One of the best prior art techniques capable of achieving a good quality/bit rate trade-off is the so-called Code Excited Linear Prediction (CELP) technique. According to this technique, the speech signal is sampled and processed in blocks of L samples (i.e. vectors), where L is some predetermined number. The CELP technique makes use of a codebook. A codebook, in the CELP context, is an indexed set of L-sample-long sequences which will be referred to as L-dimensional codevectors (pulse combinations defining L different positions and comprising both zero-amplitude pulses and non-zero-amplitude pulses assigned to respective positions p=1, 2, ...L of the combination). The codebook comprises an index k ranging from 1 to M, where M represents the size of the codebook sometimes expressed as a number of bits b: M = 2 b A codebook can be stored in a physical memory (e.g. a look-up table), or can refer to a mechanism for relating the index to a corresponding codevector (e.g. a formula). To synthesize speech according to the CELP technique, each block of speech samples is synthesized by filtering the appropriate codevector from the codebook through time varying filters modelling the spectral characteristics of the speech signal. At the encoder end, the synthetic output is computed for all or a subset of the candidate codevectors from the codebook (codebook search). The retained codevector is the one producing the synthetic output that is the closest to the original speech signal according to a perceptually weighted distortion measure. A first type of codebooks is the so-called "stochastic" codebooks. A drawback of these codebooks is that they often involve substantial physical storage. They are stochastic, i.e. random in the sense that the path from the index to the associated codevector involves look-up tables that are the result of randomly generated numbers or statistical techniques applied to large speech training sets. The size of stochastic codebooks tends to be limited by storage and/or search complexity. A second type of codebooks are the algebraic codebooks. By contrast with the stochastic codebooks, algebraic codebooks are not random and require no storage. An algebraic codebook is a set of indexed codevectors in which the amplitudes and positions of the pulses of the k th codevector can be derived from its index k through a rule requiring no, or minimal, physical storage. Therefore, the size of an algebraic codebook is not limited by storage requirements. Algebraic codebooks can also be designed for efficient search. OBJECTS OF THE INVENTION An object of the present invention is therefore to provide a method and device for drastically reducing the complexity of the codebook search upon encoding a sound signal, these method and device being applicable to a large class of codebooks. SUMMARY OF THE INVENTION More particularly, in accordance with the present invention, there is provided a method of conducting a search in a codebook in view of encoding a sound signal. The codebook contains a set of pulse amplitude/position combinations defining a number L of different positions p and comprising both zero-amplitude pulses and non-zero-amplitude pulses assigned to respective positions p = 1, 2, ...L of the combination. Each non-zero-amplitude pulse assumes one of q possible amplitudes. This codebook search conducting method comprises pre-selecting from the codebook a subset of pulse amplitude/position combinations in relation to the sound signal, and searching only this subset of pulse amplitude/position combinations in view of encoding the sound signal whereby complexity of the search is reduced as only a subset of the pulse amplitude/position combinations of the codebook is searched. Pre-selecting a subset of pulse amplitude/position combinations comprises pre-establishing, in relation to the sound signal, an amplitude/position function between the positions p = 1, 2, ...L and the q possible amplitudes. Pre-establishing an amplitude/position function comprises pre-assigning one of the q possible amplitudes as valid amplitude to each position p. Pre-assigning one of the q possible amplitudes to each position p comprises (a) processing the sound signal to produce a backward-filtered target signal D and a pitch-removed residual signal R', (b) calculating an amplitude estimate vector B in response to the backward-filtered target signal D and to the pitch-removed residual signal R', and (c) for each position p, quantizing an amplitude estimate B p of the vector B to obtain the amplitude to be selected for that position p. Finally, searching the subset of pulse amplitude/position combinations comprises limiting the search to the pulse amplitude/position combinations of the codebook having non-zero-amplitude pulses which satisfy the pre-established function. The present invention also relates to a device for conducting a search in a codebook in view of encoding a sound signal. The codebook contains a set of pulse amplitude/position combinations each defining a number L of different positions p and comprising both zero-amplitude pulses and non-zero-amplitude pulses assigned to respective positions p = 1, 2, ...L of the combination. Each non-zero-amplitude pulse assumes one of q possible amplitudes. This codebook search conducting device comprises means for pre-selecting from the codebook a subset of pulse amplitude/position combinations in relation to the sound signal, and means for searching only the subset of pulse amplitude/position combinations in view of encoding the sound signal whereby complexity of the search is reduced as only a subset of the pulse amplitude/position combinations of the codebook is searched. The pre-selecting means comprises means for pre-establishing, in relation to the sound signal, an amplitude/position function between the positions p = 1, 2, ...L and the q possible amplitudes, and the pre-establishing means comprises means for pre-assigning one of the q possible amplitudes as valid amplitude to each position p. The means for pre-assigning one of the q possible amplitudes to each position p comprises (a) means for processing the sound signal to produce a backward-filtered target signal D and a pitch-removed residual signal R', ( b) means for calculating an amplitude estimate vector B in response to the backward-filtered target signal D and to the pitch-removed residual signal R', and ( c) means for quantizing, for each of the positions p, an amplitude estimate B p of the vector B to obtain the amplitude to be selected for the position p. Finally, the searching means comprises means for limiting the search to the pulse amplitude/position combinations of the codebook having non-zero-amplitude pulses which satisfy the pre-established function. Advantageously, the pre-established function is satisfied when the non-zero-amplitude pulses of a pulse amplitude/position combination each have an amplitude equal to the amplitude pre-assigned by the pre-established function to the position p of said non-zero-amplitude pulse. According to a preferred embodiment, the amplitude estimate vector B is calculated by summing the backward-filtered target signal D in normalized form: (1-β) D ∥D∥ to the pitch-removed residual signal R' in normalized form: β R' ∥R'∥ to thereby obtain an amplitude estimate vector B of the form: B=(1-β) D ∥D∥ +β R' ∥R"∥ where β is a fixed constant having a value situated between 0 and 1. According to another preferred embodiment, for the amplitude vector estimate is quantized, for each position p, by quantizing a peak-normalized amplitude estimate B p of vector B using the following expression: wherein the denominator is a normalizing factor representing a peak amplitude of the non-zero-amplitude pulses. According to a third preferred embodiment, the method further comprises restraining the positions p of the non-zero-amplitude pulses of the combinations of the codebook in accordance with a set of tracks of pulse positions. The pulse positions of each track may be interleaved with the pulse positions of the other tracks. The pulse combinations may each comprise a number N of non-zero-amplitude pulses, the set of tracks may comprise N tracks of pulse positions respectively associated to the N non-zero-amplitude pulses, and the pulse positions of each non-zero-amplitude pulse are restrained to the positions of the associated track. According to a fourth preferred embodiment: the pulse amplitude/position combinations each comprise a number N of non-zero-amplitude pulses; the subset of pulse amplitude/position combinations is searched by maximizing a given ratio having a denominator α k 2 computed by means of N nested loops in accordance with the following relation: α 2 k = U'(p 1 ,p 1 ) + U'(p 2 ,p 2 ) + 2U'(p 1 ,p 2 ) + U'(p 3 ,p 3 ) + 2U'(p 1 ,p 3 ) + 2U'(p 2 ,p 3 ) ... ... ... ... + U'(p N ,p N ) + 2U'(p 1 ,p N ) + 2U'(p 2 ,p N ) + ... + 2U'(p N-1 ,p N ) where computation for each loop is written in a separate line from an outermost loop to an innermost loop of the N nested loops, where p n is the position of the n th non-zero-amplitude pulse of the combination, and where U'(p x ,p y ) is a function dependent on the amplitude S p x pre-assigned to a position p x amongst the positions p and the amplitude S p y pre-assigned to a position py amongst the positions p; and maximizing the given ratio comprises skipping at least the innermost loop of the N nested loops whenever the following inequality is true where S p n is the amplitude pre-assigned to position p n , D p n is the p n th component of the target vector D, and T D is a threshold related to the backward-filtered target vector D. The present invention further relates to a cellular communication system for servicing a large geographical area divided into a plurality of cells, comprising: mobile transmitter/receiver units; cellular base stations respectively situated in the cells; means for controlling communication between the cellular base stations; a bidirectional wireless communication sub-system between each mobile unit situated in one cell and the cellular base station of that cell, this bidirectional wireless communication sub-system comprising in both the mobile unit and the cellular base station (a) a transmitter including means for encoding a speech signal and means for transmitting the encoded speech signal, and (b) a receiver including means for receiving a transmitted encoded speech signal and means for decoding the received encoded speech signal. The speech signal encoding means comprises means responsive to the speech signal for producing speech signal encoding parameters, and these speech signal encoding parameter producing means comprises a device as described hereinabove, for conducting a search in a codebook in view of producing at least one of the speech signal encoding parameters, wherein the speech signal constitutes the sound signal. According to the invention, there are further provided: A cellular network element comprising (a) a transmitter including means for encoding a speech signal and means for transmitting the encoded speech signal, and (b) a receiver including means for receiving a transmitted encoded speech signal and means for decoding the received encoded speech signal. The speech signal encoding means comprises means responsive to the speech signal for producing speech signal encoding parameters, and these speech signal encoding parameter producing means comprises a device as described hereinabove, for conducting a search in a codebook in view of producing at least one of the speech signal encoding parameters, wherein the speech signal constitutes the sound signal. A cellular mobile transmitter/receiver unit comprising (a) a transmitter including means for encoding a speech signal and means for transmitting the encoded speech signal, and (b) a receiver including means for receiving a transmitted encoded speech signal and means for decoding the received encoded speech signal. The speech signal encoding means comprises means responsive to the speech signal for producing speech signal encoding parameters, and these speech signal encoding parameter producing means comprises the above described device for conducting a search in a codebook in view of producing at least one of the speech signal encoding parameters, wherein the speech signal constitutes the sound signal. In a cellular communication system for servicing a large geographical area divided into a plurality of cells, and comprising: mobile transmitter/receiver units; cellular base stations respectively situated in these cells; and means for controlling communication between the cellular base stations; a bidirectional wireless communication sub-system between each mobile unit situated in one cell and the cellular base station of that cell, this bidirectional wireless communication sub-system comprising in both the mobile unit and the cellular base station (a) a transmitter including means for encoding a speech signal and means for transmitting the encoded speech signal, and (b) a receiver including means for receiving a transmitted encoded speech signal and means for decoding the received encoded speech signal. The speech signal encoding means comprises means responsive to the speech signal for producing speech signal encoding parameters, and these speech signal encoding parameter producing means comprises the above described device for conducting a search in a codebook in view of producing at least one of the speech signal encoding parameters, wherein the speech signal constitutes the sound signal. The foregoing and other objects, advantages and features of the present invention will become more apparent upon reading of the following non-restrictive description of a preferred embodiment thereof, given by way of example only with reference to the accompanying drawings. BRIEF DESCRIPTION OF THE DRAWINGS In the appended drawings: Figure 1 is a schematic block diagram of a sound signal-encoding device comprising an amplitude selector and an optimizing controller in accordance with the present invention; Figure 2 is a schematic block diagram of a decoding device associated with the encoding device of Figure 1; Figure 3a is a sequence of basic operations for the fast codebook search in accordance with the present invention, based on signal-selected pulse amplitudes; Figure 3b is a sequence of operations for pre-assigning one of the q amplitudes to each position p of the pulse amplitude/position combinations; Figure 3c is a sequence of operations involved in the N-embedded loop search in which the innermost loop is skipped whenever the contribution of the first N-1 pulses to the numerator DA k T is deemed insufficient; Figure 4 is a schematic representation of the N-nested loops used in the codebook search; and Figure 5 is a schematic block diagram illustrating the infrastructure of a typical cellular communication system. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT Figure 5 illustrates the infrastructure of a typical cellular communication system 1. Although application of the search conducting method and device according to the invention to a cellular communication system is disclosed as a non limitative example in the present specification, it should be kept in mind that these method and device can be used with the same advantages in many other types of communication systems in which sound signal encoding is required. In a cellular communication system such as 1, a telecommunications service is provided over a large geographic area by dividing that large area into a number of smaller cells. Each cell has a cellular base station 2 (Figure 5) for providing radio signalling channels, and audio and data channels. The radio signalling channels are utilized to page mobile radio telephones (mobile transmitter/receiver units) such as 3 within the limits of the cellular base station's coverage area (cell), and to place calls to other radio telephones either inside or outside the base station's cell, or onto another network such as the Public Switched Telephone Network (PSTN) 4. Once a radio telephone 3 has successfully placed or received a call, an audio or data channel is set up with the cellular base station 2 corresponding to the cell in which the radio telephone 3 is situated, and communication between the base station 2 and radio telephone 3 occurs over that audio or data channel. The radio telephone 3 may also receive control or timing information over the signalling channel whilst a call is in progress. If a radio telephone 3 leaves a cell during a call and enters another cell, the radio telephone hands over the call to an available audio or data channel in the new cell. Similarly, if no call is in progress a control message is sent over the signalling channel such that the radio telephone logs onto the base station 2 associated with the new cell. In this manner mobile communication over a wide geographical area is possible. The cellular communication system 1 further comprises a terminal 5 to control communication between the cellular base stations 2 and the Public Switched Telephone Network 4, for example during a communication between a radio telephone 3 and the PSTN 4, or between a radio telephone 3 in a first cell and a radio telephone 3 in a second cell. Of course, a bidirectional wireless radio communication sub-system is required to establish communication between each radio telephone 3 situated in one cell and the cellular base station 2 of that cell. Such a bidirectional wireless radio communication system typically comprises in both the radio telephone 3 and the cellular base station 2 (a) a transmitter for encoding the speech signal and for transmitting the encoded speech signal through an antenna such as 6 or 7, and (b) a receiver for receiving a transmitted encoded speech signal through the same antenna 6 or 7 and for decoding the received encoded speech signal. As well known to those of ordinary skill in the art, voice encoding is required in order to reduce the bandwidth necessary to transmit speech across the bidirectional wireless radio communication system, i.e. between a radio telephone 3 and a base station 2. The aim of the present invention is to provide an efficient digital speech encoding technique with a good subjective quality/bit rate trade-off for example for bidirectional transmission of speech signals between a cellular base station 2 and a radio telephone 3 through an audio or data channel. Figure 1 is a schematic block diagram of a digital speech-encoding device suitable for carrying out this efficient technique. The speech encoding device of Figure 1 is the same encoding device as illustrated in Figure 1 of U.S. parent patent application No. 07/927,528 to which an amplitude selector 112 in accordance with the present invention has been added. U.S. parent patent application No. 07/927,528 was filed on September 10, 1992 for an invention entitled "DYNAMIC CODEBOOK FOR EFFICIENT SPEECH CODING BASED ON ALGEBRAIC CODES". The analog speech signal is sampled and block processed. It should be understood that the present invention is not limited to an application to speech signal. Encoding of other types of sound signal can also be contemplated. In the illustrated example, the block of input sampled speech S (Figure 1) comprises L consecutive samples. In the CELP literature, L is designated as the "subframe" length and is typically situated between 20 and 80. Also, the blocks of L samples are referred to as L-dimensional vectors. Various L-dimensional vectors are produced in the course of the encoding procedure. A list of these vectors, which appear in Figures 1, and 2, as well as a list of transmitted parameters is given hereinbelow: List of the main L-dimensional vectors: S Input speech vector; R' Pitch-removed residual vector; X Target vector; D Backward-filtered target vector; Ak Codevector of index k from the algebraic codebook; and Ck Innovation vector (filtered codevector). List of transmitted parameters: k Codevector index (input of the algebraic codebook); g Gain; STP Short term prediction parameters (defining A(z)); and LTP Long term prediction parameters (defining a pitch gain b and a pitch delay T). DECODING PRINCIPLE: It is believed preferable to describe first the speech decoding device of Figure 2 illustrating the various steps carried out between the digital input (input of demultiplexer 205) and the output sampled speech (output of synthesis filter 204). The demultiplexer 205 extracts four different parameters from the binary information received from a digital input channel, namely the index k, the gain g, the short term prediction parameters STP, and the long term prediction parameters LTP. The current L-dimensional vector S of speech signal is synthesized on the basis of these four parameters as will be explained in the following description. The speech decoding device of Figure 2 comprises a dynamic codebook 208 composed of an algebraic code generator 201 and an adaptive prefilter 202, an amplifier 206, an adder 207, a long term predictor 203, and a synthesis filter 204. In a first step, the algebraic code generator 201 produces a codevector A k in response to the index k. In a second step, the codevector A k is processed by an adaptive prefilter 202 supplied with the long term prediction parameters LTP to produce an output innovation vector C k . The purpose of the adaptive prefilter 202 is to dynamically control the frequency content of the output innovation vector C k so as to enhance speech quality, i.e. to reduce the audible distortion caused by frequencies annoying the human ear. Typical transfer functions F(z) for the adaptive prefilter 202 are given below: F b (z) = 1 (1-b o z T ) F a (z) is a formant prefilter in which 0 < γ1 < γ2 < 1 are constants. This prefilter enhances the formant regions and works very effectively specially at coding rate below 5 kbit/s. Fb(z) is a pitch prefilter where T is the time varying pitch delay and b 0 is either constant or equal to the quantized long-term pitch prediction parameter from the current or previous subframes. F b (z) is very effective to enhance pitch harmonic frequencies at all rates. Therefore, F(z) typically includes a pitch prefilter sometimes combined with a formant prefilter, namely: F(z) = F a (z) F b (z) In accordance with the CELP technique, the output sampled speech signal S and is obtained by first scaling the innovation vector C k from the codebook 208 by the gain g through the amplifier 206. The adder 207 then adds the scaled waveform gC k to the output E (the long term prediction component of the signal excitation of the synthesis filter 204) of a long term predictor 203 supplied with the LTP parameters, placed in a feedback loop and having a transfer function B(z) defined as follows: B(z) = bz -T where b and T are the above defined pitch gain and delay, respectively. The predictor 203 is a filter having a transfer function being in accordance with the last received LTP parameters b and T to model the pitch periodicity of speech. It introduces the appropriate pitch gain b and delay T of samples. The composite signal E + gC k constitutes the signal excitation of the synthesis filter 204 which has a transfer function 1/A(z) (A(z) being defined in the following description). The filter 204 provides the correct spectrum shaping in accordance with the last received STP parameters. More specifically, the filter 204 models the resonant frequencies (formants) of speech. The output block S and is the synthesized sampled speech signal, which can be converted into an analog signal with proper anti-aliasing filtering in accordance with a technique well known in the art. There are many ways to design an algebraic code generator 201. An advantageous method, disclosed in the above-mentioned U.S. patent application No. 07/927,528, consists of using at least one N-interleaved single-pulse permutation code. This concept will be illustrated by way of a simple algebraic code generator 201. In this example, L = 40 and the set of 40-dimensional codevectors contains only N = 5 non-zero-amplitude pulses that will be called S p 1 , S p 2 , S p 3 , S p 4 , S p 5 . In this more thorough notation, p i stands for the location of the i th pulse within the subframe (i.e., p i ranges from 0 to L-1). Suppose that pulse S p 1 is constrained to eight possible positions p 1 as follows: p 1 = 0,5,10,15,20,25,30,35 = 0+8m 1 ;m 1 = 0,1...7 Within these eight positions, which can be called "track" #1, S p1 and seven zero-amplitude pulses can freely permute. This is a "single-pulse permutation code". Let us now interleave five such "single pulse permutation codes" by also constraining the positions of the remaining pulses in a similar fashion (i.e. track #2, track #3, track #4, and track #5). p 1 = 0,5,10,15,20,25,30,35 = 0+8m 1 p 2 = 1,6,11,16,21,26,31,36 = 1+8m 2 p 3 = 2,7,12,17,22,27,32,37 = 2+8m 3 p 4 = 3,8,13,18,23,28,33,38 = 3+8m 4 p 5 = 4,9,14,19,24,29,34,39 = 4+8m 5 Note that the integers m i = 0, 1, ..., 7 fully define the position p i of each pulse S p 1 . Thus, a simple position index kp can be derived through straightforward multiplexing of the m i 's using the following relation: k p = 4096 m 1 + 512 m 2 + 64 m 3 + 8 m 4 + m 5 It should be pointed out that other codebooks can be derived using the above pulse tracks. For instance, only 4 pulses can be used, where the first three pulses occupy the positions in the first three tracks, respectively, while the fourth pulse occupies either the fourth or the fifth track with one bit to specify which track. This design gives rise to a 13 bit position codebook. In the prior art, the non-zero-amplitude pulses were assumed to have a fixed amplitude for all practical purposes for reasons of codevector search complexity. Indeed, if pulse S p 1 may assume one of q possible amplitudes, as many as q N pulse-amplitude combinations will have to be considered in the search. For instance, if the five pulses of the first example are allowed to take one of q = 4 possible amplitudes, for example S p 1 =+1,-1,+2,-2 instead of a fixed amplitude, the algebraic codebook size jumps from 15 to 15+(5x2) bits = 25 bits; that is, a search a thousand time more complex. The present specification discloses the surprising fact that very good performance can be achieved with q-amplitude pulses without paying a heavy price. The solution consists of limiting the search to a restrained subset of codevectors. The method of selecting the codevectors is related to the input speech signal as will be described in the following description. A practical benefit is to enable an increase of the size of the dynamic algebraic codebook 208 by allowing individual pulses to assume different possible amplitudes without increasing the codevector search complexity. ENCODING PRINCIPLE: The sampled speech signal S is encoded on a block by block basis by the encoding system of Figure 1 that is broken down into 11 modules numbered from 102 to 112. The function and operation of most of these modules are unchanged with respect to the description of U.S. parent patent application No. 07/927,528. Therefore, although the following description will at least briefly explain the function and operation of each module, it will concentrate on the matter that is new with respect to the disclosure of U.S. parent patent application No. 07/927,528. For each block of L samples of speech signal, a set of Linear Predictive Coding (LPC) parameters, called short term prediction (STP) parameters, is produced in accordance with a prior art technique through an LPC spectrum analyser 102. More specifically, the analyser 102 models the spectral characteristics of each block S of L samples. The input block S of L-sample is whitened by a whitening filter 103 having the following transfer function based on the current values of the STP parameters: where a 0 = 1, and z is the usual variable of the so-called z-transform. As illustrated in Figure 1, the whitening filter 103 produces a residual vector R. A pitch extractor 104 is used to compute and quantize the LTP parameters, namely the pitch delay T and the pitch gain g. The initial state of the extractor 104 is also set to a value FS from an initial state extractor 110. A detailed procedure for computing and quantizing the LTP parameters is described in U.S. parent patent application No. 07/927,528 and is believed to be well known to those of ordinary skill in the art. Accordingly, it will not be further described in the present disclosure. A filter responses characterizer 105 (Figure 1) is supplied with the STP and LTP parameters to compute a filter responses characterization FRC for use in the later steps. The FRC information consists of the following three components where n = 1, 2, ... L. f(n): response of F(z) Note that F(z) typically includes the pitch prefilter. where γ is a perceptual factor. More generally, h(n) is the impulse response of F(z)W(z)/A(z) which is the cascade of prefilter F(z), perceptual weighting filter W(z) and synthesis filter 1/A(z). Note that F(z) and 1/A(z) are the same filters as used in the decoder of Figure 2. U(i,j): autocorrelation of h(n) according to the following expression: for 1 ≤ i ≤ L and i ≤ j ≤ L ; h(n)=0 for n<1 The long term predictor 106 is supplied with the past excitation signal (i.e. E + gC k of the previous subframe) for form the new E component using proper pitch delay T and gain b. The initial state of the perceptual filter 107 is set to the value FS supplied from the initial state extractor 110. The pitch removed residual vector R'= R-E calculated by a subtractor 121 (Figure 1) is then supplied to the perceptual filter 107 to obtain at the output of the latter filter a target vector X. As illustrated in Figure 1, the STP parameters are applied to the filter 107 to vary its transfer function in relation to these parameters. Basically, X = R' - P where P represents the contribution of the long term prediction (LTP) including "ringing" from the past excitations. The MSE criterion which applies to Δ can now be stated in the following matrix notations: where H is an L x L lower-triangular Toeplitz matrix formed from the h(n) response as follows. The term h(0) occupies the matrix diagonal and h(1), h(2), ...h(L-1) occupy the respective lower diagonals. A backward filtering step is performed by the filter 108 of Figure 1. Setting to zero the derivative of the above equation with respect to the gain g yields to the optimum gain as follows: ∂∥Δ∥ 2 ∂g =0 g = X(A k H T ) T ∥A k H T ∥ 2 With this value for g, the minimization becomes: The objective is to find the particular index k for which the minimization is achieved. Note that because ∥X∥ 2 is a fixed quantity, the same index can be found by maximizing the following quantity: where D = (XH) and α k 2 = ∥A k H T ∥ 2 In the backward filter 108, a backward filtered target vector D = (XH) is computed. The term "backward filtering" for this operation comes from the interpretation of (XH) as the filtering of time-reversed X. Only an amplitude selector 112 has been added to Figure 1 of the above mentioned U.S. parent patent application No. 07/927,528. The function of the amplitude selector 112 is to restrain the codevectors A k being searched by the optimizing controller 109 to the most promising codevectors A k to thereby reduce the codevector search complexity. As described in the foregoing description, each codevector A k is a pulse amplitude/position combination waveform defining L different positions p and comprising both zero-amplitude pulses and non-zero-amplitude pulses assigned to respective positions p = 1, 2, ...L of the combination, wherein each non-zero-amplitude pulse assumes at least one of q different possible amplitudes. Referring now to Figure 3a, 3b and 3c, the purpose of the amplitude selector 112 is to pre-establish a function S p between the positions p of the codevector waveform and the q possible values of the pulse amplitudes. The pre-established function S p is derived in relation to the speech signal prior to the codebook search. More specifically, pre-establishing this function consists of pre-assigning, in relation to the speech signal, at least one of the q possible amplitudes to each position p of the waveform (step 301 of Figure 3a). To pre-assign one of the q amplitudes to each position p of the waveform, an amplitude estimate vector B is calculated in response to the backward-filtered target vector D and to the pitch-removed residual vector R'. More specifically, the amplitude estimate vector B is calculated by summing (substep 301-1 of Figure 3b) the backward-filtered target vector D in normalized form: (1-β) D ∥D∥ and the pitch-removed residual vector R' in normalized form: β R' ∥R'∥ to thereby obtain an amplitude estimate vector B of the form: B=(1-β) D ∥D∥ +β R' ∥R'∥ where β is a fixed constant having a typical value of 1/2 (the value of β is chosen between 0 and 1 depending on the percentage of non-zero-amplitude pulses used in the algebraic code), For each position p of the waveform, the amplitude S p to be pre-assigned to that position p is obtained by quantizing a corresponding amplitude estimate B p of vector B. More specifically, for each position p of the waveform, a peak-normalized amplitude estimate B p of the vector B is quantized (substep 301-2 of Figure 3b) using the following expression: wherein Q (.) is the quantization function and is a normalisation factor representing a peak amplitude of the non-zero-amplitude pulses. In the important special case in which: q = 2, that is the pulse amplitudes can assume only two values (i.e. S p i =±1); and the non-zero-amplitude pulse density N/L is lower than or equal to 15%; the value of β can be equal to zero; then the amplitude estimate vector B reduces simply to the backward-filtered target vector D and consequently S p = sign(D p ). The purpose of the optimizing controller 109 is to select the best codevector A k from the algebraic codebook. The selection criterion is given in the form of a ration to be calculated for each codevector A k and to be maximized over all codevectors (step 303): where D = (XH) and α 2 k =∥A k H T ∥ 2 . Since A k is an algebraic codevector having N non-zero-amplitude pulses of respective amplitudes S p i , the numerator is the square of and the denominator is an energy term which can be expressed as: where U(p i ,p j ) is the correlation associated with two unit-amplitude pulses, one at position pi and the other at position pj. This matrix is computed in accordance with the above equation in the filter response characterizer 105 and included in the set of parameters referred to as FRC in the block diagram of Figure 1. A fast method for computing this denominator (step 304) involves the N-nested loops illustrated in Figure 4 in which the trim lined notation S(i) and SS(i,j) is used in the place of the respective quantities "S p i " and "S p i S p j ". Computation of the denominator α k 2 is the most time consuming process. The computations contributing to α k 2 which are performed in each loop of Figure 4 can be written on separate lines from the outermost loop to the innermost loop as follows: α 2 k = S p 1 2 U(p 1 ,p 1 ) + S p 2 2 U(p 2 ,p 2 ) + 2S p 1 S p 2 U(p 1 ,p 2 ) + S p 3 2 U(p 3 ,p 3 ) + 2[S p 1 S p 3 U(p 1 ,p 3 ) +S p 2 S p 3 U(p 2 ,p 3 )] ... ... ... ... + S p N 2 U(p N ,p N ) + 2[S p 1 S p N U(p 1 ,p N ) +S p 2 S p N U(p 2 ,p N ) + ... +S p N-1 S p N U(p N-1 ,p N )] where p i is the position of the i th non-zero-amplitude pulse. Note that the N-nested loops of Figure 4 enables constraining the non-zero-amplitude pulses of codevectors A k in accordance with N interleaved single-pulse permutation codes. In the present invention search complexity is drastically reduced by restraining the subset of codevectors A k being searched to codevectors of which the N non-zero-amplitude pulses respect the function pre-established in step 301 of Figure 3a. The pre-established function is respected when the N non-zero-amplitude pulses of a codevector A k each have an amplitude equal to the amplitude pre-assigned to the position p of the non-zero-amplitude pulse. Said restraining the subset of codevectors is preformed by first combining the pre-established function S p with the entries of matrix U(i,j) (step 302 of Figure 3a) then, by using the N-nested loops of Figure 4 with all pulses S(i) assumed to be fixed, positive and of unit amplitude (step 303). Thus, even though the amplitude of non-zero pulses can take any of q possible values in the algebraic codebook, the search complexity is reduced to the case of fixed pulse amplitudes. More precisely, the matrix U(i,j) which is supplied by the filter response characterizer 105 is combined with the pre-established function in accordance with the following relation (step 302): U'(i,j)=S i S j U (i,j) where S i results from the selecting method of amplitude selector 112, namely S i is the amplitude selected for an individual position i following quantization of the corresponding amplitude estimate. With this new matrix, the computation for each loop of the fast algorithm can be written on a separate line, from the outermost to the innermost loop, as follows: α 2 k = U'(p 1 ,p 1 ) + U'(p 2 ,p 2 ) + 2U'(p 1 ,p 2 ) + U'(p 3 ,p 3 ) + 2U'(p 1 ,p 3 ) + 2U'(p 2 ,p 3 ) ... ... ... ... + U'(p N ,p N ) + 2U'(p 1 ,p N ) + 2U'(p 2 ,p N ) + ... + 2U'(p N-1 ,p N ) where p x is the position of the x th non-zero-amplitude pulse of the waveform, and where U'(p x ,p y ) is a function dependent on the amplitude S p x pre-assigned to a position p x amongst the positions p and the amplitude S p y pre-assigned to a position py amongst the positions p. To still further reduce the search complexity, one may skip (cf Figure 3c) in particular, but not exclusively, the innermost loop whenever the following inequality is true: where S p n is the amplitude pre-assigned to position p n , D p n is the p n th component of the target vector D, and TD is a threshold related to the backward-filtered target vector D. The global signal excitation signal E + gCk is computed by an adder 120 (Figure 1) from the signal gCk from the controller 109 and the output E from the predictor 106. The initial state extractor module 110, constituted by a perceptual filter with a transfer function 1/A(zγ -1 ) varying in relation to the STP parameters, subtracts from the residual signal R the signal excitation signal E + gCk for the sole purpose of obtaining the final filter state FS for use as initial state in filter 107 and pitch extractor 104. The set of four parameters k, g, LTP and STP are converted into the proper digital channel format by a multiplexer 111 completing the procedure for encoding a block S of samples of speech signal.

Claims: A method of conducting a search in a codebook in view of encoding a sound signal, in which: the codebook contains a set of pulse amplitude/position combinations (A k ); each pulse amplitude/position combination (A k ) defines a number L of different positions p and comprises both zero-amplitude pulses and non-zero-amplitude pulses assigned to respective positions p = 1, 2, ...L of the combination; each non-zero-amplitude pulse assumes one of q possible amplitudes; and said codebook search conducting method comprises: pre-selecting from said codebook a subset of pulse amplitude/position combinations (A k ) in relation to the sound signal; and searching only said subset of pulse amplitude/position combinations (A k ) in view of encoding the sound signal whereby complexity of the search is reduced as only a subset of the pulse amplitude/position combinations of the codebook is searched; wherein: pre-selecting a subset of pulse amplitude/position combinations (A k ) comprises pre-establishing, in relation to the sound signal, an amplitude/position function (S p ) between the positions p = 1, 2, ...L and the q possible amplitudes; pre-establishing an amplitude/position function (S p ) comprises pre-assigning one of the q possible amplitudes as valid amplitude to each position p; and pre-assigning one of the q possible amplitudes to each position p comprises: processing the sound signal to produce a backward-filtered target signal D and a pitch-removed residual signal R'; calculating an amplitude estimate vector B in response to the backward-filtered target signal D and to the pitch-removed residual signal R'; and for each of said positions p, quantizing an amplitude estimate B p of said vector B to obtain the amplitude to be selected for said position p; and searching said subset of pulse amplitude/position combinations (A k ) comprises limiting the search to the pulse amplitude/position combinations (A k ) of said codebook having non-zero-amplitude pulses which satisfy the pre-established function (S p ). The method of claim 1, wherein the pre-established function (S p ) is satisfied when the non-zero-amplitude pulses of a pulse amplitude/position combination (A k ) each have an amplitude equal to the amplitude pre-assigned by the pre-established function (S p ) to the position p of said non-zero-amplitude pulse. The method of claim 1 or 2, in which calculating an amplitude estimate vector B comprises summing the backward-filtered target signal D in normalized form: (1-β) D ∥D∥ to the pitch-removed residual signal R' in normalized form: β R' ∥R'∥ to thereby obtain an amplitude estimate vector B of the form: B=(1-β) D ∥D∥ +β R' ∥R'∥ where β is a fixed constant. The method of claim 3, wherein β is a fixed constant having a value situated between 0 and 1. The method of one of claims 1 to 4, in which for each of said positions p, quantizing an amplitude vector estimate comprises quantizing a peak-normalized amplitude estimate B p of said vector B using the following expression: wherein the denominator is a normalizing factor representing a peak amplitude of the non-zero-amplitude pulses. The method of one of claims 1 to 5, further comprising restraining the positions p of the non-zero-amplitude pulses of the combinations (A k ) of the codebook in accordance with a set of tracks of pulse positions. The method of claim 6, wherein the pulse positions of each track are interleaved with the pulse positions of the other tracks. The method of claim 6, wherein: said pulse combinations (A k ) each comprise a number N of non-zero-amplitude pulses; the set of tracks comprises N tracks of pulse positions respectively associated to the N non-zero-amplitude pulses; the pulse positions of each track are interleaved with the pulse positions of the N-1 other tracks; and restraining the position p comprises restraining the pulse positions of each non-zero-amplitude pulse to the positions of the associated track. The method of one of claims 1 to 8, wherein said pulse amplitude/position combinations (A k ) each comprise a number N of non-zero-amplitude pulses, and wherein searching said subset of pulse amplitude/position combinations (A k ) comprises maximizing a given ratio having a denominator α k 2 computed by means of N nested loops in accordance with the following relation: α 2 k = U'(p 1 ,p 1 ) + U'(p 2 ,p 2 ) + 2U'(p 1 ,p 2 ) + U'(p 3 ,p 3 ) + 2U'(p 1 ,p 3 )+ 2U'(p 2 ,p 3 ) ... ... ... ... + U'(p N ,p N ) + 2U'(p 1 ,p N ) + 2U'(p 2 ,p N ) + ... + 2U'(p N-1 ,p N ) where computation for each loop is written in a separate line from an outermost loop to an innermost loop of the N nested loops, where p n is the position of the n th non-zero-amplitude pulse of the combination, and where U□(p x ,p y ) is a function dependent on the amplitude S p x pre-assigned to a position p x amongst the positions p and the amplitude S p y pre-assigned to a position py amongst the positions p. The method of claim 9, wherein maximizing said given ratio comprises skipping at least the innermost loop of the N nested loops whenever the following inequality is true where S p n is the amplitude pre-assigned to position p n , D p n is the p n th component of the target vector D, and T D is a threshold related to the backward-filtered target vector D. A device for conducting a search in a codebook in view of encoding a sound signal, in which: the codebook contais a set of pulse amplitude/position combinations (A k ); each pulse amplitude/position combination (A k ) defines a number L of different positions p and comprises both zero-amplitude pulses and non-zero-amplitude pulses assigned to respective positions p = 1, 2, ...L of the combination; each non-zero-amplitude pulse assumes one of q possible amplitudes; and said codebook search conducting device comprises: means for pre-selecting from said codebook a subset of pulse amplitude/position combinations (A k ) in relation to the sound signal; and means for searching only said subset of pulse amplitude/position combinations (A k ) in view of encoding the sound signal whereby complexity of the search is reduced as only a subset of the pulse amplitude/position combinations of the codebook is searched; wherein: the pre-selecting means comprises means for pre-establishing, in relation to the sound signal, an amplitude/position function (S p ) between the positions p = 1, 2, ...L and the q possible amplitudes; the pre-establishing means comprises means for pre-assigning one of the q possible amplitudes as valid amplitude to each position p; and the means for pre-assigning one of the q possible amplitudes to each position p comprises: means for processing the sound signal to produce a backward-filtered target signal D and a pitch-removed residual signal R'; means for calculating an amplitude estimate vector B in response to the backward-filtered target signal D and to the pitch-removed residual signal R'; and means for quantizing, for each of said positions p, an amplitude estimate B p of said vector B to obtain the amplitude to be selected for said position p; and the searching means comprises means for limiting the search to the pulse amplitude/position combinations (A k ) of said codebook having non-zero-amplitude pulses which satisfy the pre-established function (S p ). The device of claim 11, wherein the pre-established function (S p ) is satisfied when the non-zero-amplitude pulses of a pulse amplitude/position combination (A k ) each have an amplitude equal to the amplitude pre-assigned by the pre-established function (S p ) to the position p of said non-zero-amplitude pulse. The device of claim 11 or 12, in which the means for calculating an amplitude estimate vector B comprises means for summing the backward-filtered target signal D in normalized form: (1-β) D ∥D∥ to the pitch-removed residual signal R' in normalized form: β R' ∥R'∥ to thereby obtain an amplitude estimate vector B of the form: B=(1-β) D ∥D∥ +β R' ∥R'∥ where β is a fixed constant. The device of claim 13, wherein β is a fixed constant having a value situated between 0 and 1. The device of one of claims 11 to 14, in which the means for quantizing an amplitude vector estimate comprises means for quantizing, for each of said positions p, a peak-normalized amplitude estimate B p of said vector B using the following expression: wherein the denominator is a normalizing factor representing a peak amplitude of the non-zero-amplitude pulses. The device of one of claims 11 to 15, further comprising means restraining the positions p of the non-zero-amplitude pulses of the combinations (A k ) of the codebook in accordance with a set of tracks of pulse positions. The device of claim 16, wherein the pulse positions of each track are interleaved with the pulse positions of the other tracks. The device of claim 16, wherein: said pulse combinations (A k ) each comprise a number N of non-zero-amplitude pulses; the set of tracks comprises N tracks of pulse positions respectively associated to the N non-zero-amplitude pulses; the pulse positions of each track are interleaved with the pulse positions of the N-1 other tracks; and the means for restraining the position p comprises a structure for restraining the pulse positions of each non-zero-amplitude pulse to the positions of the associated track. The device of one of claims 11 to 18, wherein said pulse amplitude/position combinations (A k ) each comprise a number N of non-zero-amplitude pulses, and wherein the means for searching said subset of pulse amplitude/position combinations (A k ) comprises means for maximizing a given ratio having a denominator α k 2 computed by means of N nested loops in accordance with the following relation: α 2 k = U'(p 1 ,p 1 ) + U'(p 2 ,p 2 ) + 2U'(p 1 ,p 2 ) +U'(p 3 ,p 3 ) + 2U'(p 1 ,p 3 ) + 2U'(p 2 ,p 3 ) ... ... ... ... + U'(p N ,p N ) + 2U'(p 1 ,p N ) + 2U'(p 2 ,p N ) +...+ 2U'(p N-1 ,p N ) where computation for each loop is written in a separate line from an outermost loop to an innermost loop of the N nested loops, where p n is the position of the n th non-zero-amplitude pulse of the combination, and where U'(p x ,p y ) is a function dependent on the amplitude S p x pre-assigned to a position p x amongst the positions p and the amplitude S p y pre-assigned to a position p y amongst the positions p. The device of claim 19, wherein the means for maximizing said given ratio comprises means for skipping at least the innermost loop of the N nested loops whenever the following inequality is true where S p n is the amplitude pre-assigned to position p n , D p n is the p n th component of the target vector D, and T D is a threshold related to the backward-filtered target vector D. A cellular communication system for servicing a large geographical area divided into a plurality of cells, comprising: mobile transmitter/receiver units (3); cellular base stations (2) respectively situated in said cells; means (5) for controlling communication between the cellular base stations (2); a bidirectional wireless communication sub-system between each mobile unit (3) situated in one cell and the cellular base station (2) of said one cell, said bidirectional wireless communication sub-system comprising in both the mobile unit (3) and the cellular base station (2) (a) a transmitter including means for encoding a speech signal and means for transmitting the encoded speech signal, and (b) a receiver including means for receiving a transmitted encoded speech signal and means for decoding the received encoded speech signal; wherein said speech signal encoding means comprises means responsive to the speech signal for producing speech signal encoding parameters, and wherein said speech signal encoding parameter producing means comprises a device as recited in any of claims 11 to 20, for conducting a search in a codebook in view of producing at least one of said speech signal encoding parameters, wherein the speech signal constitutes said sound signal. A cellular network element (2) comprising (a) a transmitter including means for encoding a speech signal and means for transmitting the encoded speech signal, and (b) a receiver including means for receiving a transmitted encoded speech signal and means for decoding the received encoded speech signal; wherein said speech signal encoding means comprises means responsive to the speech signal for producing speech signal encoding parameters, and wherein said speech signal encoding parameter producing means comprises a device as recited in any of claims 11 to 20, for conducting a search in a codebook in view of producing at least one of said speech signal encoding parameters, wherein the speech signal constitutes said sound signal. A cellular mobile transmitter/receiver unit (3) comprising (a) a transmitter including means for encoding a speech signal and means for transmitting the encoded speech signal, and (b) a receiver including means for receiving a transmitted encoded speech signal and means for decoding the received encoded speech signal; wherein said speech signal encoding means comprises means responsive to the speech signal for producing speech signal encoding parameters, and wherein said speech signal encoding parameter producing means comprises a device as recited in any of claims 11 to 20, for conducting a search in a codebook in view of producing at least one of said speech signal encoding parameters, wherein the speech signal constitutes said sound signal. A cellular communication system for servicing a large geographical area divided into a plurality of cells, and comprising: mobile transmitter/receiver units (3); cellular base stations (2) respectively situated in said cells; and means (5) for controlling communication between the cellular base stations (2); a bidirectional wireless communication sub-system between each mobile unit (3) situated in one cell and the cellular base station (2) of said one cell, said bidirectional wireless communication sub-system comprising in both the mobile unit (3) and the cellular base station (2) (a) a transmitter including means for encoding a speech signal and means for transmitting the encoded speech signal, and (b) a receiver including means for receiving a transmitted encoded speech signal and means for decoding the received encoded speech signal; wherein said speech signal encoding means comprises means responsive to the speech signal for producing speech signal encoding parameters, and wherein said speech signal encoding parameter producing means comprises a device as recited in any of claims 11 to 20, for conducting a search in a codebook in view of producing at least one of said speech signal encoding parameters, wherein the speech signal constitutes said sound signal.

Inventors: ADOUL JEAN-PIERRE, LAFLAMME CLAUDE, ADOUL, JEAN-PIERRE, LAFLAMME, CLAUDE
Applicants: UNIV SHERBROOKE, UNIVERSITE DE SHERBROOKE
Application year: 1996
Main classification: G10L19
IPC codes: G10L19