Frequency conversion & modulation circuits

Abstract: In a frequency conversion circuit and a modulation circuit, a filter having an impulse response (HB(z); HL(z)) corresponding to a rectangular pulse wave multiplied by a cosine wave of f 3 /4 is a band pass type filter having a center frequency of f 3 /4, and the transfer function H(z) of the filter is expressed in the form of a sum of series. When a numerator part of the transfer function is arranged to be processed with a low-speed sampling frequency f 2 and a denominator part is to be processed with a high-speed sampling frequency f 3 (= L x f 2 , L: odd number), the circuit can be made to have an adjustment-free structure and small in size. Further, when an output of processing of the numerator part based on the low-speed sampling frequency f 2 is subjected to a D/A conversion while processing of the denominator part based on the high-speed f 3 is implemented by a switched capacitor circuit, power consumption can be reduced.

Description: The present invention relates to frequency conversion & modulation circuits for use in a radio transmitter such as a car telephone or a portable telephone. Fig. 12 shows an arrangement of a prior art modulator, which includes an input terminal 1 for input of digital base band send signal connected to a digital-to-analog (D/A) converter 2, an analog multiplier 4 connected to a low-pass filter (LPF) 3, a clock generation circuit 5 connected to the D/A converter 2, an oscillator 6 connected to the analog multiplier 4, and an output terminal 7 for output of analog modulated wave connected to the analog multiplier 4. Explanation will be made below as to the operation of the prior art modulator having such an arrangement as mentioned above. First, when a digital base band send signal (such as a A/D-converted voice or modem signal) is applied to the input terminal 1, the D/A converter 2 receives the digital base band send signal from the input terminal 1, converts it to a sample value signal on the basis of a sampling clock of 384 kHz received from the clock generation circuit 5, and then sends the sample value signal to the LPF 3 where the sample value signal is subjected to interpolating operation to obtain an analog base band send signal. The analog base band send signal is further multiplied at the analog multiplier 4 by a sinusoidal wave of 24 MHz received from the oscillator 6 to be frequency-converted into a modulated wave having a center frequency of 24 MHz. The modulated wave is output from the output terminal 7. As mentioned above, even the above prior art can operate as a modulation circuit. With the above prior art modulation circuit, however, the sample value output of the D/A converter is required to act to cause the interpolating LPF to have such an abrupt characteristic curve as to suppress a harmonic spectrum having frequencies corresponding to a multiple of a relatively low sampling frequency of 384 kHz. In this connection, since a DC offset voltage applied to an operational amplifier in the circuit causes deterioration of the modulated wave, e.g., carrier leak; it is disadvantageously difficult for the circuit to realize its miniaturization and adjustment-free configuration. EP-0631377 discloses a frequency modulation method for a digital carrier signal. There is produced, by the method, a complex valued FM intermediate frequency signal. This signal is band limited and interpolated by a cascaded low pass filter or by a complex interpolation filter. ICAASP 80 Proceedings, 9-11 April 1980, Vol. 1, pages 271 to 274, E.B. Hogenauer: "A Class of Digital Filters for Decimation and Interpolation" discloses a specific class of Finite Impulse Response (FIR) Filters. SUMMARY OF THE INVENTION The present invention, as defined in the appendent claim has been made to solve the above problem in the prior art and, it is an object of the present invention to provide frequency conversion & modulation circuits which can be realized in small-sized and adjustment-free configurations. In accordance with the present invention, the above object is attained, in view of the fact that the transfer function of a filter of a delay-distortion-free, rectangular impulse response type can be given in the form of a sum of series without any multiplication, by forming the filter in the form of a sum of series of the transfer function and by extracting a harmonic spectrum while interpolating a digital send signal to execute frequency conversion, whereby the circuit can be made small in size and to have an adjustment-free structure. When the digital band pass send signal is interpolated to make the sampling frequency high, the characteristic curve of the interpolating filter after the D/A conversion can be made gentle and thus the circuit can be miniaturized. Further, when one of frequencies of a harmonic spectrum corresponding to an integer multiple of the sampling frequency is extracted during the interpolation of the digital band pass send signal, the frequency conversion is carried out to obtain a band pass signal and then the signal is subjected to the D/A conversion. Thus, a D.C. offset voltage later applied to an operational amplifier or the like can be prevented from causing deterioration of the modulated wave, e.g., carrier leak and thus the circuit can have an adjustment-free structure. Furthermore, when the digital filter for performing the above interpolation and frequency conversion is of a delay-distortion-free, rectangular impulse response type which is arranged in the form of a sum of series indicative of the filter transfer function, the filter can be implemented without using any multiplier and with delay circuits and adders/subtractors. In addition, since the numerator of the transfer function operates with a low-speed clock signal, the numbers of delay circuits and adders/subtractors can be remarkably reduced when compared to those in an ordinary filter structure based on "sum of products" calculation, with the result that the circuit can be made smaller in size with less power consumption. Since multiplication is unnecessary and a less number of adders/subtractors is required, the filter calculation can be carried out based on integer operation without any operational error only by increasing the word length (number of adders/subtractors) of the adders/subtractors by the number of bits. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a block diagram of an arrangement of a frequency conversion circuit in accordance with a first embodiment of the present invention; Fig. 2 is a timing chart of signals appearing in the first embodiment of the present invention; Fig. 3 shows a waveform of impulse response to a transfer function HB(z) in the first embodiment of the present invention; Figs. 4A and 4B are characteristic diagrams showing relationships between the frequency and gain of a transfer function HB(z) in the first embodiment of the present invention; Figs. 5A and 5B are characteristic diagrams showing relationships between the frequency and gain of a transfer function H(z) in the first embodiment of the present invention; Figs. 6A, 6B and 6C show filter configurations for implementing the transfer function in the first embodiment of the present invention; Fig. 7 is a block diagram of an arrangement of a part of a modulation circuit in accordance with a second embodiment of the present invention; Fig. 8 is a block diagram of an arrangement of a part of a modulation circuit in accordance with a third embodiment of the present invention; Fig. 9 is a waveform of impulse response to a transfer function HL(z) in the third embodiment of the present invention; Fig 10 is a characteristic diagram showing a relationship between the frequency and gain of the transfer function HL(z) in the third embodiment of the present invention; Fig. 11 is a characteristic diagram showing a relationship between the frequency and gain of a transfer function H(z) in the third embodiment of the present invention; Fig. 12 is a block diagram of an arrangement of a prior art modulation circuit. DESCRIPTION OF THE PREFERRED EMBODIMENTS A frequency conversion circuit in accordance with a first embodiment of the present invention will be explained with reference to a block diagram of Fig. 1 and a timing chart of Fig. 2. In the frequency conversion circuit of the first embodiment, a 12-bit digital band pass send signal having a sampling frequency of 768 kHz, a center frequency of 192 kHz and a band width of 16 kHz is subjected to a frequency conversion to a 24 MHz digital band pass send signal having a sampling frequency of 96 MHz (=768 kHz x 125) and a center frequency of 24 MHz, subjected to a D/A conversion, and then passed through a band pass filter (BPF) of a center frequency 24 MHz to obtain an analog send signal. The digital filter in the first embodiment has a transfer function H(z) which is expressed as: H ( z ) = HB ( z ) *HB ( z ) *HB ( z ) HB ( z ) = 1 + z -250 1 + z -2 = 1 - z -2 + z -4 - ... + z -248 where z -1 indicates a delay of (96 MHz) -1 . Fig. 3 is a waveform of impulse response to a transfer function HB(z), Figs. 4A and 4B are frequency-gain characteristic diagrams for the transfer function, and Figs. 5A and 5B are frequency-gain characteristic diagrams for the transfer function H(z). The present filter is a BPF having a center frequency of 24 MHz. Since points of a harmonic spectrum spaced from the center frequency by a multiple of 384 kHz correspond to notch frequencies of the transfer function H(z), it will be seen that these spectrum points are attenuated by 70 dB or more. Figs. 6A, 6B and 6C are configurations for implementing the transfer function expressed by the equation (1), wherein Fig. 6A is a mere cascade-connection configuration, Fig. 6B is a direct type configuration of the transfer functions HB(z) of Fig. 6A, and Fig. 6C corresponds to Fig. 6B but numerator parts of the transfer function H(z) operating at the sampling frequency of 768 kHz are rearranged as connected in its preceding stage while denominator parts of the transfer function H(z) operating at the sampling frequency of 96 MHz are rearranged as connected in its latter stage. In the present embodiment, the configuration of Fig. 6C is employed. In Fig. 1, an input terminal 101 for input of digital band pass send signal is connected to a delay register 102 and a clock generation circuit 120. A delay register 103 is of a 12-bit type. The delay register 102, which is of a 12-bit type, is connected to the input terminal 101, delay register 103 and clock generation circuit 120. An adder 104 is of a 13-bit type. The delay register 103 is connected to the delay register 102, adder 104 and clock generation circuit 120. A delay register 105 is of a 13-bit type and a adder 107 is of a 14-bit type. The adder 104 is connected to the input terminal 101, delay register 103, delay register 105 and adder 107. A delay register 106 is of a 13-bit type. The delay register 105 is connected to the adder 104, delay register 106 and clock generation circuit 120. The delay register 106 is connected to the delay register 105, adder 107 and clock generation circuit 120. A delay register 108 is of a 14-bit type and an adder 110 is of a 15-bit type. The adder 107 is connected to the adder 104, delay register 105, delay register 106, delay register 108 and adder 110. A delay register 109 is of a 14-bit type. The delay register 108 is connected to the adder 107, delay register 109, adder 110 and clock generation circuit 120. The delay register 109 is connected to the delay register 108, adder 110 and clock generation circuit 120. A switch (SW) 111 is for insertion of 0 signal. The adder 110 is connected to the adder 107, delay register 108, delay register 109 and switch 111. A subtractor 112 is of a 16-bit type. The switch 111 is connected to the adder 110, subtractor 112 and clock generation circuit 120. A delay register 113 is of a 16-bit type and a subtractor 114. The subtractor 112 is connected to the switch 111, delay register 113 and subtractor 114. A delay register 115 is of a 17-bit type. The delay register 113 is connected to the subtractor 112, subtractor 114, delay register 115 and clock generation circuit 120. A subtractor 116 is of a 18-bit type. The subtractor 114 is connected to the delay register 113, delay register 115 and subtractor 116. The delay register 115 is connected to the subtractor 114, subtractor 116 and clock generation circuit 120. A delay register 117 is of a 18-bit type and a D/A converter 118 is of a 12-bit type. The subtractor 116 is connected to the delay register 115, delay register 117 and D/A converter 118. The delay register 117 is connected to the subtractor 116, D/A converter 118, and clock generation circuit 120. A BPF 119 is of an analog type. The D/A converter 118 is connected to the subtractor 116, delay register 117, analog BPF 119 and clock generation circuit 120. Reference numeral 120 denotes a clock generation circuit. The analog BPF 119 is connected to the D/A converter 118 and clock generation circuit 120. The clock generation circuit 120 is connected to the delay register 102, delay register 103, delay register 105, delay register 106, delay register 108, delay register 109, switch 111, delay register 113, delay register 115, delay register 117 and D/A converter 118. Numeral 121 denotes an output terminal for output of analog modulated wave, which terminal is connected to the analog BPF 119. Explanation will then made as to the operation of the present embodiment. In Fig. 1, when the input terminal 101 for input of digital band pass send signal, first of all, receives one sample at a rising edge of a 768 kHz clock signal from the clock generation circuit 120, the adder 104 adds contents of the delay register 103 to the input signal, the adder 107 adds contents of the delay register 109 to an output of the adder 107, the adder 110 adds contents of the delay register 109 to an output of the adder 107 and outputs the addition to the switch 111, such that, at a falling edge of the 768 kHz clock signal, an output of the delay register 108 is applied to the delay register 109, the output of the adder 107 is to the delay register 108, an output of the delay register 105 to the delay register 106, the output of the adder 104 is to the delay register 105, an output of the delay register 102 is to the delay register 103, and an input signal received from the input terminal 101 is sent to the delay register 102. The switch 111 outputs the output of the adder 110 for a time corresponding to one clock of a 96 MHz clock signal from the rising edge point of the 768 kHz clock signal, but outputs zero for a time corresponding to the remaining 124 clocks as 96 MHz sampling output signal. Further, at the rising edge of the 96 MHz clock signal received from the clock generation circuit 120, the subtractor 112 subtracts contents of the delay register 113 from the output of the switch 111, the subtractor 114 subtracts contents of the delay register 115 from an output of the subtractor 112, the subtractor 116 subtracts contents of the delay register 117 from an output of the subtractor 114 and outputs its subtraction result to the D/A converter 118. At the falling edge of the 96 MHz clock signal, the output of the subtractor 116 is applied to the delay register 117, the output of the subtractor 114 is to the delay register 115, the output of the subtractor 112 is to the delay register 113. An output of the D/A converter 118 is passed through the analog BPF 119 having a center frequency of 24 MHz to form an analog send signal. In this way, in accordance with the first embodiment of the present invention, by performing interpolating operation over the digital band pass send signal to make the sampling frequency high, the characteristic curve of the analog BPF 119 can be made gentle to realize a small-sized circuit. Further, during the interpolation of the digital band pass send signal, one of frequencies of a harmonic spectrum corresponding to a multiple of the sampling frequency is extracted for frequency conversion to obtain a band pass signal and then the signal is subjected to the D/A conversion. For this reason, a DC offset voltage applied later to an operational amplifier or the like will cause any deterioration of the modulated wave, e.g., carrier leak, thus realizing an adjustment-free circuit. When the digital filter (comb filter) for performing the aforementioned interpolation and frequency-conversion is of a group-delay-distortion-free, rectangular impulse response type and is implemented in the form of a sum of series indicative of its filter transfer function, this filter can eliminate the need for provision of any multipliers and can be realized with use of delay circuits and adders/subtractors alone. That is, frequency conversion can be carried out without any need of adjustment with use of the delay-distortion-free digital filter. Further, since this digital filter, in spite of the sampling frequency of 96 MHz, operates at 768 kHz for half of the processing thereof, the filter only requires 3 delay circuits and 2 subtractors per stage HB(z), that is, a total of 9 delay circuits and 6 subtractors, with the result that the entire circuit can be made small in size and low in power consumption. In addition, when the subtractor having a word length of a maximum of 18 bits is prepared, the calculation can be executed without error. (Second Embodiment) Explanation will then be made as to a second embodiment of the present invention. Shown in Fig. 7 is a block diagram of an arrangement of a frequency conversion circuit in a modulation circuit of the present embodiment. In the modulation circuit of the present embodiment, a 12-bit digital band pass send signal having a sampling frequency of 48 kHz and a band width of 16 kHz is subjected to a frequency conversion to a digital band pass send signal having a sampling frequency of 96 MHz (=384 kHz x 250) and a center frequency of 24 MHz, subjected to a D/A conversion, and then passed through a BPF having a center frequency of 24 MHz to obtain an analog send signal. The transfer function H(z) of a digital filter in the present embodiment is expressed by an equation (2) which follows. H ( z ) = HB ( z ) *HB ( z ) *HB ( z ) HB ( z ) = 1 + z -8 1 + z -2 = 1 - z -2 + z -4 - z -6 where z -1 denotes a delay of (384 kHz) -1 . In Fig. 7, reference numeral 301 denotes an input terminal for input of digital band pass send signal, numeral 302 denotes a 12-bit delay register 302, and 320 denotes a clock generation circuit. The input terminal 301 is connected to the delay register 302 and clock generation circuit 320. Numeral 303 denotes a 12-bit delay register. The delay register 302 is connected to the input terminal 301, delay register 303 and clock generation circuit 320. Numeral 304 denotes a 13-bit adder. The delay register 303 is connected to the delay register 302, adder 304 and clock generation circuit 320. Numeral 305 denotes a 13-bit delay register, and 307 denotes a 14-bit adder. The adder 304 is connected to the input terminal 301, delay register 303, delay register 305 and adder 307. Numeral 306 denotes a 13-bit delay register. The delay register 305 is connected to the adder 304, delay register 306 and clock generation circuit 320. The delay register 306 is connected to the delay register 305, adder 307 and clock generation circuit 320. Numeral 308 denotes a 14-bit delay register and 310 denotes a 15-bit adder. The adder 307 is connected to the adder 304, delay register 305, delay register 306, delay register 308 and adder 310. Numeral 309 denotes a 14-bit delay register. The delay register 308 is connected to the adder 307, delay register 309, adder 310 and clock generation circuit 320. The delay register 309 is connected to the delay register 308, adder 310 and clock generation circuit 320. Numeral 311 denotes a switch (SW) for insertion of 0 signal. The adder 310 is connected to the adder 307, delay register 308, delay register 309 and switch 311. Numeral 312 denotes a 16-bit subtractor. The switch 311 is connected to the adder 310, subtractor 312 and clock generation circuit 320. Numeral 313 denotes a 16-bit delay register and 314 denotes a 17-bit subtractor. The subtractor 312 is connected to the switch 311, delay register 313 and subtractor 314. Numeral 315 denotes a 17-bit delay register. The delay register 313 is connected to the subtractor 312, subtractor 314, delay register 315 and clock generation circuit 320. Numeral 316 denotes a 18-bit subtractor. The subtractor 314 is connected to the delay register 313, delay register 315 and subtractor 316. The delay register 315 is connected to the subtractor 314, subtractor 316 and clock generation circuit 320. Numeral 317 denotes a 18-bit delay register and 318 denotes a 12-bit D/A converter. The subtractor 316 is connected to the delay register 315, delay register 317 and D/A converter 318. The delay register 317 is connected to the subtractor 316, D/A converter 318 and clock generation circuit 320. Numeral 319 denotes an analog BPF. The D/A converter 318 is connected to the subtractor 316, delay register 317, analog BPF 319 and clock generation circuit 320. Numeral 321 denotes an analog modulated wave output terminal. The analog BPF 319 is connected to the D/A converter 318 and analog modulated wave output terminal 321. The clock generation circuit 320 is connected to the delay register 302, delay register 303, delay register 305, delay register 306, delay register 308, delay register 309, switch 311, delay register 313, delay register 315, delay register 317 and D/A converter 318. The analog modulated wave output terminal 321 is connected to the analog BPF 319. The operation of the present embodiment will next be explained. In Fig. 7, when the adder 304 receives one sample from the input terminal 301 at a rising edge of a 48 kHz clock signal received from the clock generation circuit 320, the adder 304 adds contents of the delay register 303 to the input signal, the adder 307 adds contents of the delay register 306 to an output of the adder 304, the adder 310 adds contents of the delay register 309 to an output of the adder 307 and outputs its addition result to the switch 311, such that, at a falling edge of the 48 kHz clock signal, an output of the delay register 308 is applied to the delay register 309, an output of the adder 307 is to the delay register 308, an output of the delay register 305 is to the delay register 306, an output of the adder 304 is to the delay register 305, an output of the delay register 302 is to the delay register 303, and the input signal of the input terminal 301 is applied to the delay register 302. In this connection, the switch 311 outputs the output of the adder 310 for a time corresponding to one clock of the 96 MHz clock signal from the rising edge of the 48 kHz clock signal but outputs 0 for a time corresponding to the remaining 124 clocks,as 96 MHz sampling output signal. Further, at rising edges of a 96 MHz clock signal from the clock generation circuit 320, the subtractor 312 subtracts contents of the delay register 313 from the output of the switch 311, the subtractor 314 subtracts contents of the delay register 315 from the output of the subtractor 312, the subtractor 316 subtracts contents of the delay register 317 from the output of the subtractor 314 and outputs its subtraction result to the D/A converter 318, such that, at falling edges of the 96 MHz clock signal, the output of the subtractor 316 is applied to the delay register 317, the output of the subtractor 314 is to the delay register 315, and the output of the subtractor 312 is to the delay register 313. The output of the D/A converter 318 is passed through the analog BPF 319 having a center frequency of 24 MHz to form an analog send signal. As mentioned above, in accordance with the third embodiment of the present invention, the digital band pass send signal is interpolated through the digital filter in the preceding stage to obtain a band pass signal having a sampling frequency of 96 MHz and a center frequency of 24 MHz, and the frequency conversion circuit in the first embodiment is employed in the latter stage, with the result that the modulation circuit can be made small in size and to have an adjustment-free structure. (Third Embodiment) A third embodiment of the present invention will next be explained by referring to a block diagram of Fig. 8. In the modulation circuit of the third embodiment, a 12-bit digital band pass send signal having a sampling frequency of 64 kHz and a band width of 16 kHz is subjected to a frequency conversion to a digital band pass send signal having a sampling frequency of 96 MHz (=384 kHz x 250) and a center frequency of 24 MHz, subjected to a D/A conversion, and then passed through a BPF having a center frequency of 24 MHz to obtain an analog send signal. In the third embodiment, a digital band pass send signal is interpolated by a digital filter having the transfer function H(z) expressed by an equation (3) to obtain a signal having a sampling frequency of 384 kHz, multiplied by 1, 0, -1, 0, 1, ... to obtain a 12-bit digital band pass send signal having a center frequency of 96 kHz, and then subjected to the frequency conversion by the frequency conversion circuit of the first embodiment. Although the conversion ratio of the sampling frequency based on the equation (2) is limited to a multiple of the power of 2 in the third embodiment, the sampling frequency conversion of an integer multiple is possible in the equation (3). H ( z ) = HL ( z ) *HL ( z ) *HL ( z ) HL ( z ) = 1 - z -6 1 - z -1 = 1 + z -1 + z -2 + z -4 + z -6 where z -1 denotes a delay of (384 kHz) -1 Fig. 9 is a waveform of impulse response to a transfer function HL(z), Fig. 10 is a frequency-gain characteristic diagram for the transfer function HL(z), and Fig. 11 is a frequency-gain characteristic diagram for the transfer function H(z). The present filter is a low pass filter (LPF) and a harmonic spectrum corresponding to an integer multiple of 64 kHz corresponds to notch frequencies of the H(z), the input signal is attenuated by an amount of 70 dB or more. In Fig. 8, reference numeral 501 denotes an input terminal 501 for input of digital band pass send signal, numeral 502 denotes a 12-bit delay register, 503 denotes a 13-bit subtractor, and 518 denotes an analog modulated wave output terminal. The input terminal 501 is connected to the delay register 502, subtractor 503 and analog modulated wave output terminal 518. The delay register 502 is connected to the input terminal 501, subtractor 503 and analog modulated wave output terminal 518. Numeral 504 denotes a 12-bit delay register, and 505 denotes a 14-bit subtractor. The subtractor 503 is connected to the input terminal 501, delay register 502, delay register 504 and subtractor 505. Numeral 517 denotes a clock generation circuit. The delay register 504 is connected to the subtractor 503, subtractor 505 and clock generation circuit 517. Numeral 506 denotes a 14-bit delay register, and 507 denotes a 14-bit subtractor. The subtractor 505 is connected to the subtractor 503, delay register 504, delay register 506 and subtractor 507. The delay register 506 is connected to the subtractor 505, subtractor 507 and clock generation circuit 517. Numeral 508 denotes a switch (SW). The subtractor 507 is connected to the subtractor 505, delay register 506, switch 508 and clock generation circuit 517. Numeral 509 denotes a 16-bit subtractor. The switch 508 is connected to the subtractor 507, subtractor 509 and clock generation circuit 517. Numeral 510 denotes a 16-bit delay register, and 511 denotes a 17-bit subtractor. The subtractor 509 is connected to the switch 508, delay register 510 and subtractor 511. The delay register 510 is connected to the subtractor 509, subtractor 511 and clock generation circuit 517. Numeral 512 denotes a 17-bit delay register, and 513 denotes a 18-bit subtractor. The subtractor 511 is connected to the delay register 510, delay register 512 and subtractor 513. The delay register 512 is connected to the subtractor 511, subtractor 513 and clock generation circuit 517. Numeral 514 denotes a 18-bit delay register, and 515 denotes a multiplier. The subtractor 513 is connected to the delay register 512, delay register 514 and multiplier 515. The delay register 514 is connected to the subtractor 513, multiplier 515 and clock generation circuit 517. Numeral 516 denotes a frequency conversion circuit in the first embodiment. The multiplier 515 is connected to the subtractor 513, delay register 514 and frequency conversion circuit 516. The frequency conversion circuit 516 is connected to the multiplier 515, clock generation circuit 517 and analog modulated wave output terminal 518. The clock generation circuit 517 is connected to the delay register 502, delay register 504, delay register 506, switch 508, delay register 510, delay register 512, delay register 514 and frequency conversion circuit 516. The analog modulated wave output terminal 518 is connected to the frequency conversion circuit 516. The operation of the present embodiment will then be explained. In Fig. 9 , when receiving one sample from the input terminal 501 at a rising edge of the 64 kHz clock signal from the clock generation circuit 517, the subtractor 503 subtracts contents of the delay register 502 from the input signal, the subtractor 505 subtracts contents of the delay register 504 from an output of the subtractor 503, the subtractor 507 subtracts contents of the delay register 506 from an output of the subtractor 505 and outputs its subtraction result to the switch 508, such that, at a falling edge of the 64 kHz clock signal, an output of the subtractor 505 is applied to the delay register 506, the output of the subtractor 503 is to the delay register 504, and the input signal of the input terminal 501 is to the delay register 502. The switch 508 outputs the output of the subtractor 507 for a time corresponding to one clock of the 384 kHz clock signal from the rising edge of the 64 kHz clock signal, but outputs 0 for a time corresponding to the remaining 5 clocks thereof for 384 kHz sampling output. Further, at a rising edge of the 384 kHz clock signal from the clock generation circuit 517, the subtractor 509 subtracts the contents of the delay register 510 from the output of the switch 508, the subtractor 511 subtracts the contents of the delay register 512 from the output of the subtractor 509, the subtractor 513 subtracts the contents of the delay register 514 from the output of the subtractor 511, the multiplier 515 multipliers the output of the subtractor 513 by {j n + (-j) n }/2=1, 0, -1, 0, 1, ..., such that, at a falling edge of the 384 kHz clock signal, the output of the subtractor 509 is applied to the delay register 510, the output of the subtractor 511 is to the delay register 512, the output of the subtractor 513 is to the delay register 514. Since the multiplier 515 outputs a band pass signal having a sampling frequency of 384 kHz and a center frequency of 24 MHz, the frequency conversion circuit 516 located downstream of the multiplier 515 outputs an analog send signal through an analog BPF having a center frequency of 24 MHz. As mentioned above, in accordance with the third embodiment of the present invention, the digital band pass send signal is interpolated through the digital filter in the preceding stage to obtain a band pass signal having a sampling frequency of 384 kHz and a center frequency of 24 MHz, and the frequency conversion circuit in the first embodiment is employed in the latter stage, with the result that the modulation circuit can be made small in size and to have an adjustment-free structure. Further, though the sampling frequency conversion ratio of the digital band pass send signal is limited to a multiple of the power of 2 in the third embodiment, the sampling conversion corresponding to an integer multiple is possible in the fifth embodiment. As has been explained in the foregoing, in accordance with the present invention, when the digital band pass send signal is interpolated to make the sampling frequency high, the characteristic curve of the interpolating filter after the D/A conversion can be made gentle and thus the circuit can be made small in size. Further, one of frequencies of the harmonic spectrum corresponding to an integer multiple of the sampling frequency is extracted during the interpolation of the digital band pass send signal, frequency-converted to the band pass signal and then subjected to a D/A conversion. As a result, a D.C. offset voltage applied later to an operational amplifier can be prevented from causing deterioration of the modulated wave, e.g., carrier leak and thus an adjustment-free circuit can be realized. When the digital filter for performing the above interpolation and frequency conversion is of a delay-distortion-free, rectangular impulse response type which is arranged in the form of a sum of series indicative of the transfer function of the filter, the filter can be implemented with use of delay circuits and adders/subtractors other than multipliers and the numerator part of the transfer function can operate with a low-speed clock signal, which results in that, when compared to the arrangement of an ordinary filter based on sum and accumulated calculation, the numbers of delay circuits and adders/subtractors can be remarkably reduced and accordingly the miniaturization and low power consumption of the circuit can be realized. Since multiplication is unnecessary and a less number of adders and subtractors is required, the filter calculation can be executed based on integer calculation without any calculation errors only by increasing the word length of the adders/subtractors by (log 2A) bits (A being the number of adders and subtractors). Although the modulation circuit has been implemented in a hardware manner in any of the foregoing embodiments of the present invention, the parts of the modulation circuit corresponding to the generation and interpolation of the base-band signal with a low sampling frequency as well as the low-speed operational part (numerator part of the transfer function) of the frequency conversion circuit may be implemented in a software manner using a digital signal processor (DSP) or the like. In the latter case, since the DSP as an additional circuit is required only for the high-speed operational part (denominator part of the transfer function) of the frequency conversion circuit, the circuit can be miniaturized. Further, even when it is desired, in some cases, to execute the circuit by switching between a plurality of types of modulation systems and between a plurality of sorts of transmission rates, the additional circuit can be commonly used only by switching the DSP software, thus realizing miniaturization of the circuit.

Claims: A frequency conversion circuit comprising: an input terminal (101) for having applied thereto an input digital signal obtained by sampling, at a sampling frequency of f s2 , a band pass filtered signal, a center frequency of the band pass filter being f s2 /4; first digital filter means (102-110) for deriving, from the input digital signal applied to the input terminal, with the sampling frequency f s2 , the numerator of the transfer function HB(z) N2 obtained from a cascade connection of digital filters, each having the transfer function of the numerator of HB(z), wherein N2 is an integer; second digital filter means (112-117) for deriving, from said numerator of the transfert function HB(z) N2 , with a sampling frequency f s3 =L*f s2 , L being an odd integer, the denominator of the transfer function HB(z) N2 ; the first and second digital filter means operating on the input digital signal to perform an L-time interpolation and a harmonic component extraction having a center frequency of f s3 /4, the first and the second digital filter means being coupled together in such a way that the transfer function between the output terminal of the second digital filter means, providing an output signal, and the input terminal of the first digital filter means, receiving the input digital signal, is HB(z) N2 wherein: HB ( z )= 1-(- z -2 ) L 1+ z -2 = 1 - z -2 + z -4 -...+(-z -2 ) L-1 where z -1 denotes a delay of 1/f s3 , the first digital filter means operating at the sampling frequency of f s2 ; a D/A converter (118) receiving the output signal of the second digital filter means; and an analog band pass filter means receiving the output signal of the D/A converter (118) and providing the output signal of the frequency conversion circuit. A frequency conversion circuit as claimed in claim 1, wherein the input terminal (101,301) is also suitable for having applied to it an input digital signal obtained by sampling, at a sampling frequency of f s1 , a band pass filtered signal; the frequency conversion circuit further comprising: third digital filter means (302-310) connected to the input terminal for deriving from the input digital signal applied to the input terminal, with the sampling frequency f s1 , the numerator of the transfer function HB(z) N1 obtained from a cascade connection of digital filters each having the transfer function of the numerator of HB(z), wherein N1 is an integer and L has a first value L1; and fourth digital filter means (311-317), connected between the third digital filter means and the first digital filter means, for deriving from the numerator of the transfer function HB(z) N1 , with a sampling frequency f s2 = L1*f s1 , L being an odd integer and having the value L1, the denominator of the transfer function HB(z) N1 ; wherein: the third and fourth digital filter means operate on the input digital signal to perform an L1 time interpolation and a harmonic component extraction having a centre frequency of f s2 /4; the first digital filter means derives the numerator of the transfer function HB(z) N2 from the numerator and denominator derived by the third and fourth digital filter means, and L has a second value L2; L in the second digital filter means has the second value L2, providing for the derivation of the denominator of the function HB(z) N2 with a sampling frequency of f s3 =L2*f s3 ; the first and second digital filter means operate on the digital signal output from the fourth digital filter means to perform L2 time interpolation and harmonic component extraction having the centre frequency f s3 /4; and the third and fourth digital filter means are coupled in such a way that the transfer function between the output terminal of the fourth digital filter means, providing an output signal, and the input terminal of the third digital filter means, receiving the input digital signal, is HB(z) N1 , in which z -1 denotes a delay of 1/f s2 , the third digital filter means operating at a sampling frequency of f s1 .

Inventors: INOGAI KAZUNORI, INOGAI, KAZUNORI
Applicants: MATSUSHITA ELECTRIC IND CO LTD, MATSUSHITA ELECTRIC INDUSTRIAL CO., LTD.
Application year: 1996
Main classification: H03H17
IPC codes: H03C1, H03H17, H03D7