CLOCK GENERATION CIRCUIT FOR A DISPLAY CONTROLLER HAVING A FINE TUNEABLE FRAME RATE

Abstract: A clock generation circuit for a display controller includes an intermediate dot clock generation circuit which receives an input clock signal and in response thereto generates an intermediate dot clock signal having a plurality of dot clock pulses. A row pulse generation circuit is coupled to the intermediate dot clock generation circuit and counts the intermediate dot clock signal dot clock pulses and generates a row pulse after a predetermined number of dot clock pulses and a programmable offset time. The row pulse generation circuit also generates a final dot clock signal by masking the intermediate dot clock signal with the programmable offset time after the predetermined number of dot clock pulses. A method of adjusting a rate at which data is transferred to a display screen is also disclosed.

Description: CLOCK GENERATION CIRCUIT FOR A DISPLAY CONTROLLER HAVING A FINE TUNEABLE FRAME RATE BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to display controllers, and more particularly, to a display controller having a fine tuneable frame rate. 2. Description of the Related Art One commonly used type of display panel is a liquid crystal display (LCD) panel. An LCD display panel is a rectangular grid of rectangular or square dots. Acting as a thin double-paned window, the LCD grid is actually transparent electrodes laid out in horizontal rows on one thin pane, and in vertical columns on the other. The liquid crystal formula trapped in between the panes reacts to an electrical field applied to each electrode in the rows and columns. This reaction rotates the polarization of light transmitted through the LCD display. Polarizing layers outside the panes cause the dots to appear light or dark as the polarization changes. There are small gaps between the rows and columns, giving each dot a clear definition. The display is controlled by continuously feeding dot data to the display. The data is organized as follows into individual pixels, rows of pixels, and full-page frames. Pixels are the individual data dots or bits. These bits are put together into rows. A set of rows makes up a frame. A frame is one full page of the display. LCD data is continuously sent to the LCD panel to refresh the display frame. Since most LCD displays have no on-board frame buffer memory, the display data must be continuously refreshed. To get a stable, flicker-free image, the display data is sent to the panel at a frame refresh rate (referred to herein as the "frame rate") which falls within a range normally specified by the LCD panel manufacturer. An LCD panel manufacturer may specify, for example, that best results are obtained, i.e., a stable, flicker-free image, when the display data is sent to the panel 60 to 70 times per second, or 60 Hz to 70 Hz. An LCD controller is typically used to coordinate the transfer of display data to an LCD panel. Two important functions performed by an LCD controller are: 1) gray scale modulation, and 2) sending display data to the display panel within the specified frame rate range. In order to create an image on an LCD screen, each pixel is constantly being refreshed at the frame rate. If only two different colors are needed, i.e., on (white or bright) and off (black or dark), a zero is always sent for white and a one is always sent for black. For example, assuming that each pixel is refreshed 60 times per second, i.e., a frame rate of 60 Hz, if a pixel is white, the value of zero will be sent 60 times for each second (for that bit), and if the pixel is black (or dark), a one will be sent for 60 times. In this scenario the graphics data (the one and zeros indicating white and black) can basically be fed directly to the display. However, when more than two colors are needed on the LCD screen, gray scale modulation is performed to create an LCD image that appears to be stable and appears to be some shade between on (white or bright) and off (black or dark). Gray scale modulation is a process of sending a value of one to the screen for a percentage of the time to create a pixel that is light or dark gray. The rate at which the pixels are turned on and off determines how light or dark they appear. For example, if a one is sent for 45 times, and a zero is sent for 15 times (during the 60 Hz refresh), a dark gray will appear on the screen. If a one is sent for 15 times, and a zero is sent for 45 times, a light gray will appear. In general, an LCD controller receives graphics data and then generates and provides the appropπate ones and zeros to the display panel which are needed to display the specified shade of gray for each pixel in the frame. Because of the nature of LCD displays, gray scale modulation is done in a temporal (or time) and spatial modulated way. The term "temporal" refers to the frequency at which individual pixels are turned on and off. The term "spatial" refers to the relationship of one pixel to an adjacent or nearby pixel. Specifically, in order to prevent flickering, adjacent pixels of the same gray value will be modulated at different frequencies. Thus, the brightness of each pixel in the display is determined by the temporal modulation of the applied voltage pulses to the respective pixels. The accuracy of the frame rate at which the LCD controller sends display data to the display panel is important for at least two reasons. First, as mentioned above, a stable, flicker-free image will result if the display data is sent to the panel at a frame rate which falls within the specified range. Second, the generation of gray scales is largely affected by the frame rate via temporal modulation. The frame rate generated by conventional LCD controllers often tends to vary and be inaccurate. This is because the frame rate is usually generated from an input clock which is sourced from an external source of clocking for the rest of the system with which the LCD controller is associated. Because many systems can operate at different clock frequencies, the frequency of the input clock may vary. This will cause the frame rate to vary as well. Conventional LCD controllers suffer from the disadvantage that their generated frame rates cannot be fine tuned in response to such variations in the input clock. Thus, there is a need for a display controller that is capable of having its frame rate fine tuned. SUMMARY OF THE INVENTION The present invention provides a clock generation circuit for a display controller. An intermediate dot clock generation circuit receives an input clock signal and in response thereto generates an intermediate dot clock signal having a plurality of dot clock pulses. A row pulse generation circuit is coupled to the intermediate dot clock generation circuit and counts the intermediate dot clock signal dot clock pulses and generates a row pulse after a predetermined number of dot clock pulses and a programmable offset time. The row pulse generation circuit also generates a final dot clock signal by masking the intermediate dot clock signal with the programmable offset time after the predetermined number of dot clock pulses. The present invention also provides a method of adjusting a rate at which data is transferred to a display screen. The method includes the steps of: setting a predetermined offset time; performing binary clock division on an input clock signal to generate an output binary clock divided signal; performing integer clock division on the output binary clock divided signal to generate an intermediate dot clock signal having a plurality of dot clock pulses; counting the intermediate dot clock signal dot clock pulses; generating a row pulse after a predetermined number of dot clock pulses and the predetermined offset time; and, masking the intermediate dot clock signal with the predetermined offset time after the predetermined number of dot clock pulses to generate a final dot clock signal. A better understanding of the features and advantages of the present invention will be obtained by reference to the following detailed description of the invention and accompanying drawings which set forth an illustrative embodiment in which the principles of the invention are utilized. BRIEF DESCRIPTION OF THE DRAWINGS Figure 1 is a block diagram illustrating a display controller in accordance with the present invention connected to an LCD display. Figure 2 is a block diagram illustrating shift registers included the LCD display shown in Figure 1. Figure 3 is a block diagram illustrating a pixel and row arrangement on the screen of the LCD display shown in Figure 1. Figure 4 is a timing diagram illustrating the clocking signals generated by the display controller shown in Figure 1. Figure 5 is a block diagram illustrating the partitioning of an external memory that may be used with the display controller shown in Figure 1. Figure 6 is a block diagram illustrating two words of graphics data which may be stored in the external memory shown in Figure 5. Figure 7 is a block diagram illustrating one word of gray scale look-up -able (GLUT) data which may be stored in the external memory shown in Figure 5. Figure 8 is a table illustrating a GLUT word decoding map for the GLUT word shown in Figure 7. Figure 9 is a more detailed block diagram illustrating the display controller shown in Figure 1. Figure 10 is a block diagram illustrating the configuration register block shown in Figure 9. Figures 11A-11C are tables illustrating the operation of configuration register two shown in Figure 10. Figure 12 is a table illustrating the operation of configuration register three shown in Figure 10. Figure 13 is a block diagram illustrating the timing generator shown in Figure 9. Figure 14 is a block diagram illustrating portions of the timing generator shown in Figure 13. Figure 15 is a schematic diagram illustrating the binary clock division block shown in Figure 14. Figure 16 is a schematic diagram illustrating the integer clock selection control block shown in Figure 14. Figure 17 is a schematic diagram illustrating the integer clock division generation block shown in Figure 14. Figure 18 is a schematic diagram illustrating the offset clock generation block shown in Figure 14. Figure 19 ia a timing diagram illustrating the operation of the timing generator shown in Figure 9. Figure 20 is a block diagram illustrating the bus interface shown in Figure 9. Figure 21 is a block diagram illustrating the FIFO and DMA interface control shown in Figure 9. Figure 22 is a block diagram illustrating the gray scale modulator/inverse video shown in Figure 9. Figures 23-25 are timing diagrams illustrating the operation of display controller shown in Figure 1. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT Referring to Figure 1 there is illustrated a display controller 30 in accordance with the present invention. The display controller 30 overcomes the disadvantages of conventional controllers in that its frame rate can be fine-tuned to optimize image quality for a given LCD screen given an input clock whose frequency may vary. As will be discussed in detail below, the frame rate is fine tuned by setting bits [3:0] of configuration register three to add an amount of time, or "offset", to the time between the application of voltage pulses to each row of pixels on the LCD display 32. The display controller 30 described herein, which is shown controlling the LCD display 32, is capable of controlling a variety of supertwist LCD panels. For example, a few of the supported configurations include 320x240. 320x200 and 480x320 with monochrome or grayscale graphics LCD modules equipped with self-contained screen drivers. Furthermore, the gray scale modulation scheme discussed below may also be used for a large number of 1/4 and 1/2 size VGA, XVGA, and SVGA screen sizes with excellent image quality. The display controller 30 supports inverse video displays with programmable blinking rates. Two types of screen display modes are selectable. The first type is inverse video display (See bit [1] of configuration register one, discussed below), and the second type is display in blink mode where the duration and background are selectable (See bits [7:5] of configuration register four). It should be understood, however, that the use of the display controller 30 is not limited to LCD displays or to any specific size or type of screen. It is envisioned that the teachings of the present invention may be applied to display controllers used to control other types of displays, such as TFT displays. The programming of the display controller 30 is controlled by an external CPU 33. The term "external" as used herein is intended to mean external to the display controller 30. Graphics data for the display controller 30 is preferably stored in an external memory 42, but it should be understood that the display controller 30 may include an internal memory. The external memory 42 may be either a dedicated video RAM, or part of a shared system memory 31 (e.g., a DRAM or SRAM) used by both the external CPU 33 and the display controller 30. The memory interface is preferably built through a channel in an external DMA (direct memory access) controller 35 which transfers the graphics data from the external memory 42 to the display controller 30 This minimizes CPU 33 overhead and permits the LCD display 32 to continue even with the CPU 33 in idle or power save modes. The display controller 30 may be a stand-alone device, e.g., built as its own integrated circuit (IC), or it may be incorporated or integrated into a larger IC as indicated by 37. Such an IC 37 may include other on-board components, such as for example, the CPU 33, the DMA controller 35, a DRAM controller 45, and or a bus interface unit (BIU) 47. The display controller 30 converts the graphics data stored in the external memory into display data, and then sends the display data to the LCD display 32 via the LCD[3:0] signal lines. The sequencing of the display data is controlled with three clock signals: a row pulse clock CL1, a dot clock CL2, and a frame signal CLF. The frame signal CLF indicates the start of a frame of data. The dot clock CL2 is used to clock the display data LCD[3:0] four pixels at a t me into shift registers 34 in the LCD display 32. Referring to Figure 2, as the display data LCD[3:0] is sent to the LCD display 32 in four pixel nibbles, it is sequenually organized into a full row of data in the shift registers 34 Specifically, the shift registers 34 store the nibbles until they have an entire row (320 in the example shown in Figure 2). The row pulse clock CL1 indicates when a full row of pixels has been sent. Upon the arrival of the row pulse clock CL1, the LCD display 32 outputs the contents of the shift registers 34 to the internal column dπvers 36. A row counter is incremented and the next row of display data LCD[3 0] is stored in the shift registers 34. Similarly, the row pulse clock CL1 indicates when that row is full and the contents of the shift registers 34 are again output to the internal column dπvers 36. In this way, the entire frame is sequenually wπtten. A frame consists of a given number of rows of a given number of pixels. For example, as shown in Figure 3, a 320x240 display would have a row consisung of 320 pixels. A set of 240 rows would consist of a complete display frame of 320x240. A complete frame of data makes up one full display screen. Referπng to Figure 4, the display data LCD[3:0] is clocked out of the display controller 30 and into the shift registers 34 on the falling edge of the dot clock CL2. Each dot clock CL2 pulse clocks four pixels into the internal shift registers 34 The pixels are taken from lines LCD[3:0], with the left most pixel on LCD[3]. As will be discussed below, the dot clock CL2 is deπved from two levels of input clock processing, and specifically, two levels of clock division. Bits [7.3] of configurauon register two define the level of clock division. Once all the pixels of a row have been sent, the display controller 30 applies a pulse on the row pulse clock CL1. This wπtes the row onto the display and advances to the next row. The row pulse clock CL1 is generated by counung the number of dot clock CL2 cycles. For example, because there is one dot clock CL2 pulse for every 4 pixels, there would be 80 dot clock CL2 cycles for 320 pixels. As data is presented for the first row of the frame, the frame signal CLF is brought high, and is held through the first row pulse clock CL1, as shown Because of the varying characteπsucs of each LCD display, the exact frame refresh rate generated by the display controller 30 has a significant beaπng on the final image quality of the display. Thus, in accordance with the present invention, the display controller 30 allows the programmer to expenment with the precise frame refresh rate required to opUmize image quality. Specifically, this is accomplished by allowing the programmer to add an amount of "offset" time 38 to the time between the last dot clock CL2 pulse 39 of a row and the row pulse clock CL1 41. Additional offset dot clock CL2 times are added to create a precise frame refresh rate The offset dot clock CL2 times are not addiuonal pulses, but are just the amount of ume of a dot clock CL2 pulse. In other words, the programmer may vary the time between the last dot clock CL2 and the row pulse clock CL1 by a few CL2 pulse times in order to optimize the visual image for the given display characteπstics. In this way, the dot clock CL2 start pulse 43 of the next row is shifted or stretched away from the dot clock CL2 pulse 39 of the previous row. This fine-tunes the frame refresh rate and results in excellent image quality regardless of the LCD display characteristics. Thus, the row pulse clock CL1 is generated by counting the number of dot clock CL2 cycles and any programmed untransmitted dot clock CL2 offset cycles. In the embodiment of the display controller 30 described herein, as little as 1 offset dot clock CL2 time to as many as 16 additional offset dot clock CL2 times can be added to the time between the last dot clock CL2 pulse 39 and the row pulse clock CL1 41. The programmed untransmitted dot clock CL2 offset times are programmed by setting bits [3:0] of configuration register three (discussed below). Furthermore, this time can be varied "on-the-fly" so that the programmer can see the real-time effect of different values in these bits. It should be well understood, however, that the present invention is not limited to a programmable offset time of 1 to 16 dot clock CL2 times. The range of 1 to 16 dot clock CL2 times is an example of just one embodiment of the present invention and this range may be expanded or reduced in accordance with the present invention. Furthermore, the increments of the programmed offset time, e.g., 1 pulse increments, may also be expanded or reduced in accordance with the present invention. Referring to Figure 5, the graphics data which is held in the external memory may include a section of gray scale look-up table (or "GLUT") data 40, followed by the graphics data 42 for the current frame. The number of words of GLUT data held in the external memory may be specified by the display controller 30. In some cases, the GLUT data can be the same for all data frames, and in other cases the GLUT data may be dynamically updated by the external CPU. By way of example, one word of GLUT may be used for each frame; so, if 10 GLUT words are specified, then it will be 10 frames before the GLUT data will need to be updated by the external CPU. In the embodiment of the display controller 30 described herein, the size of the GLUT is programmable from 0-16 words by setting bits [1:4] of configuration register four (discussed below). It should be well understood, however, that either more or less than 16 words of GLUT may be designated in the external memory in accordance with the present invention. Whether or not the GLUT data 40 is stored in the shared system memory or its own memory, the display controller 30 maintains a programmable gray scale modulation scheme in that memory. The gray scale levels are programmable frame-by-frame, which is a feature that most conventional LCD controllers do not have. Programmability of the gray scale levels allows greater flexibility of the controller in interfacing with different displays, environmental conditions, and user preferences. The display controller 30' s gray scale modulation scheme has several benefits over previous controllers. First, previous LCD controllers performed such temporal modulation by manipulating the graphics data with a fixed gray scale algorithm in hardware. Such fixed algorithms could not be updated or programmed. Second, there is greater efficiency in updating programmable gray scale modulation data in the display controller 30 than in the display controller with on-chip modulation data registers mentioned above. Since the GLUT data updates are performed to the GLUT data 40 stored in the external memory, versus an on-board memory, there is no interrupt to the display controller 30' s standard data accesses of gray scale data 40 and graphics data 42. Also, the standard data accesses are not interrupted so no extra frame buffering is needed inside the display controller 30 to account for the delay. In some conventional controllers, new gray scale modulation data must be written by an external processor to the LCD controller every frame. In the display controller 30, several frames of GLUT data 40, e.g., up to 16 frames or more, can be stored in the system memory, thus allowing the display controller 30 to go through 16 frames of modulation data prior to needing an update of the memory by the CPU 33. In addition, since the designated number of frames of GLUT data 40, e.g., 16 frames, may be adequate for many purposes, some users may choose to loop through the 16 programmed words of GLUT data 40 without the CPU 33 updating them because the modulation may already be acceptable. The embodiment of the display controller 30 described herein permits a user to program from 2 to 16 words of GLUT data 40, it should be well understood, however, that the invention is not limited to 16 words of GLUT data 40 and is not limited to one word of modulation data per frame, but can be expanded or reduced as needed A third advantage of the display controller 30 over conventional controllers is that it has a greater capability in programming gray scale modulation for multiple frames with little or no impact on die size Since the gray scale modulauon data, l e , GLUT data 40, is stored off-chip in an external memory, the only impact to the design in increasing the size of the programmable area is adding more word counts for the added gray scale memory space On conventional controllers with on-board frame-by-frame gray scale modulaUon data, a larger memory space would have to be created on-chip for buffeπng extra frames of gray scale modulation data As mentioned above, the display controller 30 may use a shared system memory approach to acquiπng GLUT data 40 and graphics data 42, but such shared memory is not required Furthermore, the display controller 30 is ideal for being implemented in a portable macro cell which can be easily integrated on chip with other macro functions, such as the IC 37 mentioned above Although the shared memory and the portable macro cell design are not requirements of the present invention, these features can be used for better cost and board space efficiency than convenuonal discreet LCD controller solutions which have a fixed hardware gray scale algoπthm designed for a fixed screen model and which access graphics data through a dedicated video RAM Such conventional controllers consume extra power and space (l e cost) on the system board For example, high-end personal digital assistant (PDA) applicauons have hmitauons on space and power dissipauon, and thus, could use the integrated, share system memory display controller 30 approach very efficiently Although not required, it will be assumed for the remainder of this discussion that the GLUT data 40 and the graphics data 42 may both be stored in the shared system memory The number of words of GLUT data 40 designated in the system memory may be specified by the display controller 30 In some cases, the GLUT data 40 can be the same for all data frames, and in other cases the GLUT data 40 may be dynamically updated by the external CPU 33 By way of example, one word of GLUT may be used for each frame, so, if 10 GLUT words are specified, then it will be 10 frames before the GLUT data will need to be updated by the external CPU 33 In the embodiment of the display controller 30 descπbed herein, the size of the GLUT data 40 is programmable from 0-16 words by setting bits [1 4] of configurauon register four (discussed below) It should be well understood, however, that either more or fewer than 16 words of GLUT data 40 may be designated in the system memory (or whatever memory is used to store the GLUT data 40) in accordance with the present invention Furthermore, it should be understood that more than one word of GLUT data 40 could be used per frame, or that the size of a GLUT word may be larger or smaller than 16 bits When the number of programmed GLUT words has been reached, an internal GLUT counter generates a CPU interrupt This interrupt can be programmably turned off within the display controller 30 if peπodic GLUT updaUng is not needed If the interrupt is turned off, the current GLUT data is conunuously looped through from frame to frame Referπng to Figure 6 two words 44, 46 of graphics data 42 are shown When the data is to be displayed in simple monochrome black (or dark) and white, each bit of each word 44, 46 translates into a single pixel in the display as indicated at 48 In other words, a one in the graphics data 42 translates into a full on pixel of either black or blue, and a zero in the graphics data 42 translates into a full off pixel, or a white pixel However, when simple monochrome is not sufficient, the display controller 30 also supports gray scale modulauon of the graphics data 42 Although the display controller 30 is capable of generaung many different shades of gray, the following discussion will assume that four shades of gray are generated The four shades of gray are OFF (black or dark), dark gray, light gray, and ON A gray scale pixel map is used to modulate the vaπous pixels Gray scale pixels are turned on and off duπng successive frame scans. The rate in which they are turned on and off determines how dark or light they appear. As discussed above, because of the nature of LCD displays, this modulation is done in a temporal or time modulated way. Flickering is prevented by modulating adjacent pixels of the same gray value at different frequencies using phase delay. Pixels are modulated for gray-scale by presenting their data bits high and low in successive frame scans. Although the duty cycles are the same, adjacent or nearby gray pixels will not be modulated identically, a process referred to as spatial modulation. This accomplished by modulating even and odd rows differently, as well as by modulating each pixel of four adjacent pixels differently, as will be seen in Figure 7. In order to indicate which shade of gray is to be displayed, the graphics data 42 gray-scale values will be one of the following: 00 = full bright, 01 = light gray, 10 = dark gray, 11 = off. Thus, as indicated at 50 in Figure 6, two bits of each word 44, 46 will be needed to generate one bit of the display data LCD[n]. If more than four shades of gray are used, then three or more bits of each word 44, 46 may be needed to generate one bit of the display data LCD[n]. The full bright value, 00, is mapped directly to a pixel value of 0; thus, when the graphics data 42 indicates a full bright value, i.e., 00, a 0 will always be sent on the appropriate line of the display data LCD[n]. Similarly, the off value, 11, is mapped to a pixel value of 1. The pixel values of light and dark gray, 01 and 10, respectively, are determined by a GLUT data 40 word, one of which is shown in Figure 7. The gray scale is achieved through modulation of the applied voltage pulses to the display 32. Since adjacent pixels are preferably not modulated in exactly the same way so that they will not blink in sync, or unwanted flickering may occur, an odd and even mapping scheme is used. For example, for a dark gray pixel on an even row, certain bits will be used to determine the graphic value. For a dark gray pixel on the next odd row, different bits will be used to determine the graphic value. In this way, no two consecutive rows will be modulated exactly the same. However, the frequencies can be the same for the next even row because no flickering will be perceived by the eye with the rows separated by another row (in space and in time). Furthermore, each pixel in a grouping of four adjacent pixels on one row is modulated differently. This is illustrated in Figure 7 by there being four different decode bits for the even row dark gray decode nibble, four different decode bits for the even row light gray decode nibble, four different decode bits for the odd row dark gray decode nibble, and four different decode bits for the odd row light gray decode nibble. The exact values of the gray scale pixel which will be sent on the display data lines LCD[3:0] are determined by using a GLUT word decoding map, shown in Figure 8, which illustrates that the table values are normally varied for even and odd rows. Referring to Figure 9, the display controller 30 includes a bus interface 52, a timing generator 54, a FIFO (first-in-first-out) register and DMA interface control 56, a gray scale modulator 58, and a configuration register block 60. In general, the timing generator 54 contains all of the decoders and counters that generate the CL2, CL1, and CLF clocking signals and blink pulse clocking. The FIFO register and DMA interface control 56 controls the FIFO read and write addresses, FIFO read and write command strobes, FIFO depth and threshold decoders, maintains the FIFO read address and write address difference up-down counter (used for LCD DMA DRQ handling), generates the word clock (for FIFO reads and for data shifting in the gray scale modulator 58), and FIFO empty procedures. The FIFO register and DMA interface control 56 also generates the control signals for DRQ and Eop_z assertion and desertion, the DRAM GLUT counter, GLUT size decoder, and the next frame GLUT position pointer, incoming graphics data indication, and the graphics data Iow_z counter (for Eop_z assertion handling). The gray scale modulator 58 generates the display data LCD[3:0], controls gray-scale modulation, display blinking, reverse video, and data output enabling. The configuration register block 60 contains all of the configuration registers for the controller, interrupt handler, and the data steering logic for reading back the contents of the configuration registers. The specific function of the signals shown in Figure 9 are as follows: Cpu_reset_z is a system reset input, Cs_lcd is a bus interface chip select input for the led controller block, Dack_z is a DMA acknowledge indicaUon input, Io_addr[l 0] is a bus interface address bits 1-0 input, Io_bb.e_z is a bus interface byte high enable input, Iow_z is a bus interface read strobe input, Iow_z is a bus interface wπte strobe input, Lcd_clk is an LCD clock input referenced to lx an external oscillator frequency, Test_en is an external test enable input for the display controller, Test_mode is an external test mode input for the display controller, Io_data[15 0] is a bidirectional peπpheral data bus, CLl is the display row selection pulse output. CL2 is the display dot clock (column clock) output, CLF is the display frame pulse output, LCD[3 0] is the display data output, Drq is a DMA request indication output, Eop_z is a DMA end of process indication output, and Int is a display controller interrupt indicaUon output The display controller 30 includes several resets Reset 1 is a general system reset, Cpu_reset_z When this reset is asserted all blocks are reset Cpu_reset_z is also part of Reset2 and Reset3 Reset2 is a combination of Cpu_reset_z and lcd_en If lcd_en is disabled then Reset2 is asserted In general, this reset allows the LCD clocks and data to be cleared while maintaining the state of the configurauon registers Reset3 is a combination of Cpu_reset_z, lcd_en, and fifo_empty_hold_z In general, this reset clears validity of data retrieval and transmission when fifo_empty_hold_z is asserted Referring to Figure 10, the configuration register block 60 preferably includes four configurauon registers that control the operauon of the display controller 30 and provide status lnformauon to an external CPU configuration register one 62, configurauon register two 64, configurauon register three 66, and configurauon register four 68 Some bits are "set once and leave alone,' while others can be set dynamically (on-the-fly) Specifically, the interrupt indication and enabling, dot clock CL2 divisors, dot clock CL2 offsets, reverse video, and blinking rates can be updated on-the-fly Updatable bits are bits [7 3] of configurauon register two 64, (controlling the dot clock CL2 divisors), bits [3 0] of configurauon register three 66, (controlling the row pulse clock CLl offset for adjusting the refresh rate), and bits [7 5] of configurauon register four 68 (controlling inverse video and blink rates) Furthermore, it should be noted that the GLUT data 40 size, screen size, number of gray scales, and FIFO threshold level are fixed after LCD enabling Referring to configurauon register one 62, bit [6], FERRINV, is a FIFO error interrupt disable selecuon bit A "1" disables FIFO empty interrupt Reset forces this bit to a "0" Bit [5], GLUTROT, is a fixed GLUT word rotauon selecuon bit A "1" enables the rotauon of the current GLUT word No new GLUT words are loaded into the current GLUT register when this mode is enabled At the beginning of each new frame, the even row nibble portions of the GLUT word are shifted πght and the odd row nibble portions are shifted left Reset forces this bit to a "0" Bit [4], FILL, is a GLUT interrupt status bit A "1" indicates that the external memory (e g , a DRAM) GLUT entries should be updated Reset forces this bit to a "0" Bit [3], FERR, is a FIFO interrupt status bit A "1" indicates that the FIFO has run dry Reset forces this bit to a "0" Bit [2], GINTENZ, is a GLUT update interrupt disabling selection bit A "1" disables the interrupt for signaling DRAM GLUT entry updates Reset forces this bit to a "0" Bit [1], RV, is a reverse video enable selection bit A "1" enables reverse video images on the LCD screen Reset forces this bit to a "0" Bit [0], BLNK, is a blink enable selection bit A " 1 ' enables blinking images on the LCD screen Reset forces this bit to a "0" Referring to configuration register two 64, Bits [7 6], BASEDV[1 0], are the binary clock division of basis selecuon for controlling the dot clock CL2 divisors Reset forces these bits to "0" Figure 11A illustrates the binary division which results from the vaπous settings of these bits Bits [5 3], CKDVBS[2 0], are the integer clock division of basis selecuon Reset forces these bits to "0" Figure 1 IB illustrates the integer division which results from the vaπous settings of these bits Bits [2 1], SIZEfl 0], are the screen size selection Reset forces these bits to "0" Figure 11C illustrates the setungs of these bits for the vaπous screen sizes Bit [0], GSCL, is the 1 or 2 bit per pixel selecuon A "1 " sets a 2 bit per pixel gray scale encoding, and a "0" sets a 1 bit per pixel gray scale encoding Resets forces this bit to a "0" Referring to configurauon register three 66, Bits [7:6] are reserved. Bits [5:4], FIFTHRS[1:0], set the fracuon that the FIFO may empty before a DREQ is generated Reset forces these bits to "0". Figure 12 illustrates the FIFO fill thresholds which result from the setungs of these bits. Bits [3:0], CLlOFF[3:0], set the row pulse clock CLl offset after the last dot clock CL2. A single offset is equal to one peπod of the CL2 clock. The number of offsets is equal to the binary equivalent of CLlOFF[3:0] + 1 This provides for a range of 1 to 16 offsets. Reset forces these bits to "0". Referring to configurauon register four 68, Bit [7], BLBCKG, is the background shade selection bit for blinking. A "1" sets the background shade to "1", and a "0" sets the background shade to "0". Reset forces this bit to a "0". Bit [6], BLMODE, sets the blink to inverse video or background selection bit. A "1" sets blink to inverse video, and a "0" sets blink to the background shade. Bit [5], BLTTME, sets the peπod of the blink selecuon bit. A " 1 " sets the blink peπod to 72 frames (50/50 duty cycle), and "0" sets the blink peπod to 36 frames (50/50 duty cycle) Reset forces this bit to a "0". Bit [4] is reserved. Bit [3:1], GLSIZ[2:0], sets the GLUT table size in external memory (e.g., DRAM) from 0-16 words. The table size is selected by the value of GLSIZ[2:0] (possible values are: 0,2,4,8,10,12,14, and 16). Reset forces these bits to "0". Bit [0], LEN, is the display controller enable selecuon bit. A "1" enables the controller (clock and data lines are active), and a "0" disables the controller (clocks and data lines are held low) Reset forces this bit to a "0". Referπng to Figure 13, the ummg generator 54 includes a test interface block 70, a CL2 generauon block 72, a CLl generauon block 74, a CLF generauon block 76, a frame counter 78, clock dπvers 80, and a graphics data enable 82. In general, the dot clock CL2 having whatever frequency is required by the LCD display 32 is obtained by dividing down an external system clock Lcd_clk. Using the data from the clock frequency configuration registers (i.e., configurauon registers two 64 and three 66), user software sets an appropπate divisor to obtain the required frequency. The clock divisor can be programmed on the fly, permitting use with different screens, and letUng the programmer easily optimize the screen frequency for the specific display screen being used. The ability to program on the fly allows the programmer to visually see the results of changes in the programming. The Uming generator 54 includes three stages of input clock processing to generate a targeted frame rate. The CL2 generation block 72 includes the first two stages of processing. Specifically, the CL2 generation block 72 receives the Lcd_clk signal which is a clock input referenced to lx an external oscillator frequency. The first stage of processing is standard binary clock division (i.e. 2, 4, 8) As mentioned above, the binary clock division is controlled by Bits [7:6], BASEDV[1:0], of configuration register two 64 The second stage of processing is a 50/50 duty cycle pπme/odd integer clock division of the result from the first stage of processing (i.e. 1, 2, 3, 5, 7, 9 ...). Bits [5:3], CKDVBS[2:0], of configurauon register two 64 control the integer clock division The output of the second stage of processing is a clock signal referred to as CL2_mt ("CL2 internal") The signal CL2_ιnt is idenucal to the dot clock CL2, except that CL2_ιnt is not masked by the programmed "unseen" dot clock CL2 offset times used for fine tuning the frame rate, and thus, maintains a conunuous duty cycle. The programmed "unseen" dot clock offset ttmes are used to mask CL2_ιnt, to form the dot clock CL2, duπng the third stage of input clock processing, which occurs in the CLl generation block 74 In the third stage of processing, the "unseen" dot clock CL2 offset times are generated pnor to the generation of a row pulse CLl These offset times add a configurable amount of delay measured in the number of "unseen" dot clocks CL2 pnor to the generauon of a row pulse CLl. This offset time accumulates within a frame and is used for fine tuning the resulting frame rate. Thus, the row pulse CLl is generated after a fixed number of dot clock CL2 pulses and the programmed offset, i.e., "unseen" dot clock CL2 times Duπng operation, the signals CLl, CL2, and CLF are held low when the display controller 30 is disabled The dot clock CL2 frequency is set by programming the binary and integer clock division levels in configurauon register two 64 The frame rate is fine tuned by programming the number of "unseen" dot clock CL2 offset pulses in the row pulse CLl via configuration register three 66. The timing generator 54 decoders are immediately supplied this information (i.e., asynchronously) until the first dot clock CL2 cycle after enabling the display controller 30. When the display controller 30 is enabled, the signals CLl, CL2, and CLF are enabled after two Lcd_clks on falling edge of the next Lcd_clk. After the controller is enabled the dot clock CL2 may be modified "on the fly" by re- programming the binary and integer clock division levels. Similarly, the frame rate may be fine tuned on the fly by programming the number of dot clock CL2 periods of CLl pulse offsets. This allows the frequencies of the clocks to be modified while the display controller 30 is enabled to ease the process of determining optimum frame rate. The timing generator 54 decoders are synchronously updated with information after the first dot clock CL2 cycle, using de-glitch circuity. Thus, the signals CLl, CL2, and CLF can be changed to new frequencies with no glitching. Referring to Figure 14, the functions of the test interface block 70, the CL2 generation block 72, the CLl generation block 74, the CLF generation block 76, and the frame counter 78 may be performed by a binary clock division block 120, an integer clock selection control block 122, an integer clock division generation block 124, and an offset clock generation block 126. The binary clock division block 120, a detailed schematic of which is shown in Figure 15, performs the standard binary clock division and passes the result on to the other blocks 122, 124, 126. The integer clock selection control block 122, a detailed schematic of which is shown in Figure 16, and the integer clock division generation block 124, a detailed schematic of which is shown in Figure 17, perform the 50/50 duty cycle prime/odd integer clock division. Finally, the offset clock generation block 126, a detailed schematic of which is shown in Figure 18, masks the "unseen" dot clock offset times onto CL2_int to form the dot clock CL2. Figure 19 illustrates the resulting CLl, CL2, CLF, and LCD[3:0] signals. Referring to Figures 20 through 22, the bus interface 52 is connected to a data bus Io_data[15:0]. The data bus Io_data[15:0] is connected to the external DMA controller 35 which coordinates the transfer of data and instructions between the display controller 30 and the external memory 31 and the CPU 33. A DMA interface control block 84 generates the DRQ and Eop_z signals for the external DMA controller 35. The bus interface 52 provides data to the rest of the display controller 30 via the data bus lcd_din[15:0]. Specifically, the data bus lcd_din[15:0] is connected to a FIFO memory core 90 and a GLUT register 94. The FIFO memory core 90 is controlled by a FIFO write control 98, a FIFO read control 104, and a FIFO read clock 100. The GLUT register 94 interfaces with a bitmap data decode 96 which interfaces with data drivers 102 to generate the display data LCD[3:0]. The display controller 30 uses DMA transfers to transfer GLUT data 40 from the external memory 31 to the GLUT register 94 and graphics data 42 from the external memory 31 to a FIFO memory core 90. The DMA channel may be configured in demand mode, Eop_z auto-initialization, and with IO write word transfers to the display controller 30 slave with zero wait states. Data access from the external memory 31 is done across the data bus Io_data[15:0] through the external DRAM controller 45 and the DMA controller 35. Preferably, the display controller 30 is I O mapped, and therefore, it does not maintain the address of the current graphics data 42; this is done by the DMA controller 35. Since the FIFO memory core 90 holds limited amount of graphics data 42, it needs occasional refilling. The threshold limit at which the FIFO memory core is refilled is variable. Data transfer from the external memory 31 begins with GLUT data 40 followed by the graphics data 42 for the current frame. Specifically, on the first DMA transfer to the display controller 30, the data coming into the display controller 30 will be the GLUT data 40, except for the case where zero GLUT words are programmed which would be the case for display applications with only two gray levels (i.e., on and off, only). The GLUT words coming into the display controller 30 will be counted and only the word used for modulation of the next frame will be stored. It is identified by a GLUT word address counter 86 that is automatically incremented each new frame. When the GLUT counter 86 reaches the number of GLUT words programmed, an interrupt control block 88 generates an interrupt to signal the external CPU 33 to update the GLUT data 40 in the system memory 31 By way of example, if each frame is specified to be at least 13 6ms long (at a 73 5Hz frame rate), then, assuming that a 16 word GLUT data 40 space has been allocated, the GLUT update interrupt would occur at least every 218ms This interrupt can be disabled within the display controller 30 should the current GLUT programming be adequate for an extended time While one word of GLUT decoding data per frame may be sufficient, the display controller 30 can work with two or more GLUT words per frame The GLUT data 40 is accessed from the first external memory 31 word locations pointed to by the base address stored in the DMA channel's base address register Initially, at display controller 30 enabling, the current and next frame s GLUT data 40 is loaded into the GLUT register 94 Upon initialization of the display controller 30, both the current and next frame's GLUT words are loaded into the GLUT word storage registers duπng the first two DMA Iow_z accesses All other GLUT accesses to the external memory 31 after initialization will be for the next frame's GLUT word The GLUT word for the current frame is transferred to a GLUT register 94 where it is used for gray scale modulation in a bitmap data decoder 96 As discussed above, the GLUT word is compπsed of two light gray and two dark gray nibbles of data, where one nibble is for odd rows and the other for even rows The nibble data stores the value (1 or 0) that should be placed on the LCD[3 0] data ports for that shade After an EOP cycle is complete (a DMA transfer complete signal), the next DMA access will start at the beginning of the display controller 30' s memory space where the next frame's GLUT data 40 will be loaded into the GLUT register 94 The next DMA access after an EOP will start at the base address previously loaded when DMA auto-initiahzauon is being used Referring to Figures 23-25, the FIFO and DMA initial cycles are performed as follows After RESET/disable, the FIFO read and wπte address are set to O0H in the FIFO wπte control block 98 The display controller 30 DMA channel, GLUT size, screen size, FIFO fill threshold level, and number of gray scales are programmed The display controller 30 is then enabled DRQ is forced active after the first lcd_clk sampled edge of lcd_en The first Dack_z and first Iow_z are started An initialization pulse is created that is used by DMA interface control block 84 to load the GLUT count, and prepares one-time current and next frame GLUT loading All Iow_z cycles continue until the end of the first Dack_z GLUT data 40 for current and next frame stored in the GLUT registers 94 The FIFO memory core 90 is filled to depth as controlled by the FIFO wπte control block 98 After the GLUT is loaded, the FIFO wπte address is incremented in the FIFO wπte control block 98 after each wπte strobe for the initial loading of the FIFO memory core 90 In the DMA interface control block 84, the look_ahead wπte address is compared with the fifo_depth, and when equal, DRQ will be deasserted After the first Dack_z deassertion, the look_ahead wπte address is subsequently compared with the current read address After the first Dack_z deassertion, the end_lst_dack bit is set in the DMA interface control block 84 Then, when the lcd_clockgen indicates the end of the frame by the signal equalrow, the signal valιd_frame is set indicating to the data dπvers 102 that it can start transmitting graphics data LCD[3 0] After the initial cycles, the FIFO and DMA standard cycles are performed as follows In general, the quantity of graphics data stored in the FIFO memory core 90 is monitored as its decreases This monitoring is performed by the read address counter 106 which generates a read address used for reading the graphics data stored m the FIFO memory core 90, as well as a wπte address which is generated by the FIFO wπte control 98 which is used for wπting to the graphics data stored in the FIFO memory core 90 The difference between the read address and the wπte address is computed by the FIFO wπte control block 98 When the difference between the read address and the wπte address falls below the F FO threshold level, a FIFO read/wπte difference count signal rw_dιffcnt is generated by the FIFO wπte control block 98 The DMA interface control block 84 generates a data request signal DRQ in response to the read/wπte difference count signal rw_dιffcnt in order to initiate the transfer of more graphics data to the FIFO memory core 90 Graphics data is transferred to the FIFO memory core via DMA accesses The FIFO wπte control block 98 monitors the quantity of graphics data in the FIFO memory core 90 as it increases Specifically, the wπte address is compared to the read address, and when the wπte address is equal to one address position less than the read address, an end of process signal is generated by the DMA interface control block 84 The end of process signal stops the DMA from transferπng graphics data to the FIFO memory core 90 Specifically, DRQ is forced active after the read-wπte address difference count is equal to the FIFO threshold Dack_z is asserted duπng FIFO wπte cycles, and the look-ahead write address is compared with the current read address after each Iow_z deassertion When the compaπson is equal, DRQ is deasserted and after one more Iow_z cycle, Dack_z is deasserted In time, DRQ will be forced active again as defined before This cycle occurs throughout a frame At the end of a frame memory, Eop_z is generated by the controller duπng the last DMA access of the frame The end of frame memory is determined by the DMA interface control block 84' s dram_word_cnt counter which is decremented after each FIFO wπte When this counter's value is equal to one, an Eop_z is forced The Eop_z is generated by the DMA interface control block 84 following the loading of the next to last word of bit-map data (l e , for the end of the row on line 240/200/320) After the Eop_z is received by the DMA controller 35, the DMA removes Dack_z after one more IOW_z cycle The dram_word_cnt counter will then be loaded with the DRAM word count that corresponds to the graphics data 42 needed for the size screen being used and the number of gray scales After Eop_z is asserted, the DMA auto- lnitia zes to the display controller 30 channel's base address The DMA access after the Eop_z (auto_ιnιtialιzatιon) will obtain the GLUT word for the next frame (unless 0 GLUT words have been programmed) and then the beginning of graphics data In the DMA interface control block 84, the look_ahead wπte address is compared with the current read address (i.e , data already read), and when equal, DRQ will be de-asserted The display controller 30 can hold DRQ active duπng the time the DMA controller 35 is going through auto-initialization Because the display controller 30 is released after sending out an EOP, a higher pπoπty DMA slave can take over the DMA controller 35 after the display controller 30 is released even though DRQ is still active Should the FIFO memory core 90 go empty, then a FIFO error reset is issued which causes the FIFO and DMA interface control block 56 to begin back at initialization The DMA controller 35 is forced to be auto-initialized after this occurs two times in succession The display data lines LCD[3 0] will be forced low until a new valid frame begins By way of example, using a 32 x 16 bit FIFO memory core 90, the maximum specified DRQ to Dack_z bus latency for a 480 x 320 screen with 4 gray levels is 20 usec (for a 320 X 240 screen, 40 usec) for 2 bits per pixel gray scale and a 72 Hz frame refresh rate The data cycles and FTFO reads are performed as follows After RESET/disable, the number of gray scales is programmed, then the display controller 30 is enabled The display data lines LCD[3 0] will output zeroes until the FIFO wπte control block 98 runs the first fifo read cycle coinciding with the first πsing edge of the dot clock CL2 at the beginning of the first valid frame The gray scale modulator 58 will then begin to supply graphics data 42 to the LCD display 32 starting at the upper left-hand pixel Graphics data 42 will conunue to be sent to the LCD display 32 until the occurrence of a reset The invention embodiments descπbed herein have been implemented in an integrated circuit which includes a number of additional functions and features which are descπbed in the following co-pending, commonly assigned patent applications, the disclosure of each of which is incorporated herein by reference U S patent application Seπal No 08/ , entitled "DISPLAY CONTROLLER CAPABLE OF ACCESSING AN EXTERNAL MEMORY FOR GRAY SCALE MODULATION DATA" (atty docket no NSC 1-62700), U S patent application Seπal No 08/ , entitled "SERIAL INTERFACE CAPABLE OF OPERATING IN TWO DIFFERENT SERIAL DATA TRANSFER MODES" (atty. docket no. NSC1-62800); U.S. patent application Serial No. 08/ , entitled "HIGH PERFORMANCE MULTIFUNCTION DIRECT MEMORY ACCESS (DMA) CONTROLLER" (atty. docket no. NSC 1-62900); U.S. patent application Serial No. 08/ , entitled "OPEN DRAIN MULTI-SOURCE CLOCK GENERATOR HAVING MINIMUM PULSE WIDTH" (atty. docket no. NSC 1-63000); U.S. patent application Serial No. 08/ , entitled "INTEGRATED CIRCUIT WITH MULTIPLE FUNCTIONS SHARING MULTIPLE INTERNAL SIGNAL BUSES ACCORDING TO DISTRIBUTED BUS ACCESS AND CONTROL ARBITRATION" (atty. docket no. NSC1-63100); U.S. patent application Serial No. 08/ , entitled "EXECUTION UNIT ARCHITECTURE TO SUPPORT x86 INSTRUCTION SET AND x86 SEGMENTED ADDRESSING" (atty. docket no. NSC1-63300); U.S. patent application Serial No. 08/ , entitled "BARREL SHIFTER" (atty. docket no. NSC1-63400); U.S. patent application Serial No. 08/ , entitled "BIT SEARCHING THROUGH 8, 16, OR 32-BIT OPERANDS USING A 32-BIT DATA PATH" (atty. docket no. NSC1-63500); U.S. patent application Serial No. 08/ entitled "DOUBLE PRECISION (64-BIT) SHIFT OPERATIONS USING A 32-BIT DATA PATH" (atty. docket no. NSC1-63600); U.S. patent application Serial No. 08/ , entitled "METHOD FOR PERFORMING SIGNED DIVISION" (atty. docket no. NSC 1-63700); U.S. patent application Serial No. 08/ entitled "METHOD FOR PERFORMING ROTATE THROUGH CARRY USING A 32-BIT BARREL SHIFTER AND COUNTER" (atty. docket no. NSC1-63800); U.S. patent application Serial No. 08/ , entitled "AREA AND TIME EFHCIENT FIELD EXTRACTION CIRCUIT" (atty. docket no. NSC1-63900); U.S. patent application Serial No. 08/ entitled "NON-ARITHMETTCAL CIRCULAR BUFFER CELL AVAILABILITY STATUS INDICATOR CIRCUIT" (atty. docket no. NSC 1-64000); U.S. patent application Serial No. 08/ entitled "TAGGED PREFETCH AND INSTRUCTION DECODER FOR VARIABLE LENGTH INSTRUCTION SET AND METHOD OF OPERATION" (atty. docket no. NSC1-64100); U.S. patent application Serial No. 08/ , entitled "PARTITIONED DECODER CIRCUIT FOR LOW POWER OPERATION" (atty. docket no. NSC 1-64200); U.S. patent application Serial No. 08/ entitled "CIRCUIT FOR DESIGNATING INSTRUCTION POINTERS FOR USE BY A PROCESSOR DECODER" (atty. docket no. NSCl-64300); U.S. patent application Serial No. 08/ entitled "CIRCUIT FOR GENERATING A DEMAND-BASED GATED CLOCK" (atty. docket no. NSC1-64500); U.S. patent application Serial No. 08/ , entitled "INCREMENTOR/DECREMENTOR" (atty. docket no. NSC1-64700); U.S. patent application Serial No. 08/ , entitled "A PIPELINED MICROPROCESSOR THAT PIPELINES MEMORY REQUESTS TO AN EXTERNAL MEMORY" (atty. docket no. NSC 1-64800); U.S. patent application Serial No. 08/ , entitled "CODE BREAKPOINT DECODER" (atty. docket no. NSC 1-64900); U.S. patent application Serial No. 08/ , entitled "TWO TIER PREFETCH BUFFER STRUCTURE AND METHOD WITH BYPASS" (atty. docket no. NSCl-65000); U.S. patent application Serial No. 08/ , entitled "INSTRUCTION LIMIT CHECK FOR MICROPROCESSOR" (atty. docket no. NSC1-65100); U.S. patent application Serial No. 08/ , entitled "A PIPELINED MICROPROCESSOR THAT MAKES MEMORY REQUESTS TO A CACHE MEMORY AND AN EXTERNAL MEMORY CONTROLLER DURING THE SAME CLOCK CYCLE" (atty. docket no. NSC1-65200); U.S. patent application Serial No. 08/ , entitled "APPARATUS AND METHOD FOR EFHCIENT COMPUTAΗON OF A 486™ MICROPROCESSOR COMPATIBLE POP INSTRUCTION" (atty. docket no. NSC1-65700); U.S. patent application Serial No. 08/ , entitled "APPARATUS AND METHOD FOR EFHCIENTLY DETERMINING ADDRESSES FOR MISALIGNED DATA STORED IN MEMORY" (atty. docket no. NSCl-65800); U.S. patent application Serial No. 08/ entitled "METHOD OF IMPLEMENTING FAST 486™ MICROPROCESSOR COMPATIBLE STRING OPERATION" (atty. docket no. NSC1-65900); U.S. patent application Serial No. 08/ , entitled "A PIPELINED MICROPROCESSOR THAT PREVENTS THE CACHE FROM BEING READ WHEN THE CONTENTS OF THE CACHE ARE INVALID" (atty. docket no. NSC 1-66000); U.S. patent application Serial No. 08/ , entitled "DRAM CONTROLLER THAT REDUCES THE TIME REQUIRED TO PROCESS MEMORY REQUESTS" (atty. docket no. NSC1-66300); U.S. patent application Serial No. 08/ , entitled "INTEGRATED PRIMARY BUS AND SECONDARY BUS CONTROLLER WITH REDUCED PIN COUNT" (atty. docket no. NSC1-66400); U.S. patent application Serial No. 08/ , entitled "SUPPLY AND INTERFACE CONFIGURABLE INPUT/OUTPUT BUFFER" (atty. docket no. NSC1-66500); U.S. patent application Serial No. 08/ , entitled "CLOCK GENERATION CIRCUIT FOR A DISPLAY CONTROLLER HAVING A FINE TUNEABLE FRAME RATE" (atty. docket no. NSC1-66600); U.S. patent application Serial No. 08/ , entitled "CONHGURABLE POWER MANAGEMENT SCHEME" (atty. docket no. NSC 1-66700); U.S. patent application Serial No. 08/ , entitled "BIDIRECTIONAL PARALLEL SIGNAL INTERFACE" (atty. docket no. NSC1-67000); U.S. patent application Serial No. 08/ , entitled "LIQUID CRYSTAL DISPLAY (LCD) PROTECTION CIRCUIT" (atty. docket no. NSC1-67100); U.S. patent application Serial No. 08/ entitled TN-CIRCUIT EMULATOR STATUS INDICATOR CIRCUIT" (atty. docket no. NSC1-67400); U.S. patent application Serial No. 08/ , entitled "DISPLAY CONTROLLER CAPABLE OF ACCESSING GRAPHICS DATA FROM A SHARED SYSTEM MEMORY" (atty. docket no. NSC 1-67500); U.S. patent application Serial No. 08/ , entitled "INTEGRATED CIRCUIT WITH TEST SIGNAL BUSES AND TEST CONTROL CIRCUITS" (atty. docket no. NSC 1-67600); U.S. patent application Serial no. 08/ , entitled "DECODE BLOCK TEST METHOD AND APPARATUS" (atty. docket no. NSC 1-68000). It should be understood that various alternatives to the embodiments of the invention described herein may be employed in practicing the invention. It is intended that the following claims define the scope of the invention and that structures and methods within the scope of these claims and their equivalents be covered thereby.

Claims: CLAIMS What is claimed is 1 A clock generauon circuit for a display controller, compπsing an intermediate dot clock generation circuit which receives an input clock signal and in response thereto generates an intermediate dot clock signal having a plurality of dot clock pulses, and a row pulse generation circuit coupled to the intermediate dot clock generation circuit which counts the intermediate dot clock signal dot clock pulses and generates a row pulse after a predetermined number of dot clock pulses and a programmable offset time, the row pulse generation circuit also generating a final dot clock signal by masking the intermediate dot clock signal with the programmable offset time after the predetermined number of dot clock pulses 2 A clock generation circuit in accordance with claim 1 , wherein the intermediate dot clock generation circuit compπses a binary clock division circuit coupled to receive the input clock signal and which performs binary clock division thereon to generate an output binary clock divided signal, and an integer clock division circuit coupled to receive the output binary clock divided signal and which performs integer clock division thereon to generate the intermediate dot clock signal 3 A clock generation circuit in accordance with claim 1, further compπsing a configuration register coupled to the row pulse generation circuit for programming the offset time 4 A clock generauon circuit for a display controller, compπsing a binary clock division circuit which receives an input clock signal and which performs binary clock division thereon to generate an output binary clock divided signal; an integer clock division circuit coupled to receive the output binary clock divided signal and which performs integer clock division thereon to generate an intermediate dot clock signal having a plurality of dot clock pulses; and an offset clock generation circuit coupled to the integer clock division circuit which counts the intermediate dot clock signal dot clock pulses and generates a row pulse after a predetermined number of dot clock pulses and a programmable offset time, the offset clock generation circuit also generating a final dot clock signal by masking the intermediate dot clock signal with the programmable offset time after the predetermined number of dot clock pulses 5 A clock generation circuit in accordance with claim 4, wherein the offset clock generauon circuit also generates a frame pulse to indicate that a predetermined number of row pulses have been generated 6 A method of adjusting a rate at which data is transferred to a display screen, compπsing the steps of setting a predetermined offset time, performing binary clock division on an input clock signal to generate an output binary clock divided signal, performing integer clock division on the output binary clock divided signal to generate an intermediate dot clock signal having a plurality of dot clock pulses; counting the intermediate dot clock signal dot clock pulses; generating a row pulse after a predetermined number of dot clock pulses and the predetermined offset time; and masking the intermediate dot clock signal with the predetermined offset time after the predetermined number of dot clock pulses to generate a final dot clock signal. 7. A method in accordance with claim 6, further comprising the step of: generating a frame pulse to indicate that a predetermined number of row pulses have been generated.

Inventors: SHAY MICHAEL J, SHAY, MICHAEL, J.
Applicants: NAT SEMICONDUCTOR CORP, NATIONAL SEMICONDUCTOR CORPORATION
Application year: 1996
Main classification: G09G5
IPC codes: G09G5