Control method and apparatus for controlling the motors of an air conditioner

Abstract: A control apparatus for controlling motors of an air conditioner comprises: a converter circuit (2) for converting an AC power (1) to a DC power and setting the input voltage of an input alternating current waveform to a sine wave of the same phase as that of the input current by at least switching means (2a); first and second brushless motors (3,12) for driving a compressor (33) and a blower (34); first and second inverter circuits (4,13) for converting the converted DC power to the AC powers and supplying them to the motors; and a microcomputer (25) for controlling at least the compressor and blower of the air conditioner. In order to improve the input power factor from the AC power, a PWM signal to on/off control the switching means (2a) included in the converter circuit (2) to obtain the DC powers for the inverter circuits is generated in the microcomputer on the basis of the input alternating current of the AC power and the output DC voltage (at 22) of the converter circuit and is outputted. At the same time, PWM signals to on/off control switching means (Ua-Za, Ub-Zb) of the inverter circuits (4,13) are generated in the microcomputer (25) and outputted in order to inverter control the motors.

Description: FIELD OF THE INVENTION The invention relates to a control method and an apparatus for controlling the motors for a compressor and a blower of an air conditioner, and more particularly, the invention provides that the compressor and blower, and a converter to obtain a DC voltage necessary for an inverter to drive the compressor and blower are controlled by a single microcomputer. DESCRIPTION OF THE RELATED ART Hitherto, an air conditioner has had control means of motors to drive a compressor and blower, respectively. For example, in the driving of the motor for the compressor, a commercially available AC power is converted to a DC power and the converted DC power is converted to an arbitrary AC voltage by the control means and is supplied to the motor for the compressor. A capacitor input type converter is generally used as converting means for converting the AC power to the DC power. However, since an input alternating current waveform from the AC power becomes a distorted wave, the power factor deteriorates and a harmonics current is generated. Therefore, various converters for setting an input alternating current waveform to a sine wave of the same phase as that of an input voltage, for improving the input power factor, and for reducing the harmonics have been proposed. The air conditioner using the converter drives the motors for the compressor and blower and is controlled by a microcomputer. An example of such a control will now be described in detail with reference to Fig. 10. The control apparatus of the air conditioner comprises: a converter circuit 2 for converting a commercially available AC power 1 to a DC power; a first inverter circuit 4 for converting the output DC voltage of the converter circuit 2 to a predetermined AC voltage and supplying it to a first brushless motor 3 for the compressor; a converter control circuit 5 for outputting an IGBT (a transistor) control signal in accordance with the input current (rectified current), the input voltage (rectified voltage), and the output voltage in the converter circuit 2 and on/off driving an IGBT (transistor) 2a as a switching means; a position detecting circuit 6 for detecting the position of the rotor of the first brushless motor 3 by a terminal voltage of the brushless motor 3; a microcomputer 7 for inputting the detected position detecting signals and outputting an inverter control signal (PWM signal = pulse-width modulation signal) for on/off controlling at least a plurality of transistors Ua, Va, Wa, Xa, Ya, and Za of the first inverter circuit 4 on the basis of the inputted position detecting signals; an upper arm drive circuit 8 and a lower arm drive circuit 9 for inputting such a control signal and on/off driving the transistors Ua, Va, Wa, Xa, Ya, and Za; a chopping circuit 10 for chopping as desired the onportions of output drive signals of the upper arm drive circuit 8 by a chopping signal from the microcomputer 7; a switching power circuit 11 for converting the commercial AC power 1 to a predetermined DC power; a second inverter circuit 13 for converting the output DC voltage of the switching power circuit 11 to a predetermined AC voltage and supplying it to a second brushless motor 12 for an outdoor side blower; and a brushless motor control circuit 14 for inputting position detecting signals of a rotor of the second brushless motor 12 that are generated from Hall elements 12a in the brushless motor 12, for inputting a rotational speed command signal from the microcomputer 7, and for outputting an inverter control signal to turn on/off at least a transistor 11d as switching means of the switching power circuit 11 and to turn on/off a plurality of transistors Ub, Vb, Wb, Xb, Yb, and Zb of the second inverter circuit 13 on the basis of the inputted position detecting signals. In addition to the IGBT 2a of the switching means, the converter circuit 2 comprises a rectifying circuit 2b for rectifying the commercial AC power 1 to the direct current, a reactor 2c, a diode 2d for blocking a reverse current, and a smoothing capacitor 2e. The converter circuit 2 converts the commercial AC power 1 to the DC power and supplies a predetermined DC voltage to the first inverter circuit 4. The first inverter circuit 4 is constructed by: an upper arm comprising the three transistors Ua, Va, and Wa for switching the connections between a positive terminal of the converter circuit 2 and three-phase windings a1, b1, and c1 of the first brushless motor 3; and a lower arm comprising the three transistors Xa, Ya, and Za for switching the connections between the 3-phase windings a1, b1, and c1 and a negative terminal of the converter circuit 2. The converter control circuit 5 comprises: a current detecting circuit; two voltage detecting circuits; an IGBT driving circuit; an exclusive-use IC for a converter control having a PWM signal generating circuit constructed by an oscillator, a multiplier, a comparator, etc.; and the like. The converter control circuit 5 detects the current by using a current sensor 5a, detects the voltage waveform obtained by rectifying the AC voltage, detects the output DC voltage, and generates a control signal [PWM signal: shown in Fig. 11(a)] for controlling the IGBT 2a of the converter circuit 2 by those detected current and voltage in a manner such that the input AC current from the AC power has a sine wave of the same phase as that of the input AC voltage (shown in Fig. 11(b)). The microcomputer 7 inputs the position detecting signals [shown in (a) to (c) in Fig. 12] from the position detecting circuit 6 and generates drive signals Ua1, Va1, Wa1, Xa1, Ya1, and Za1 shown in (d) to (i) in Fig. 12 to the upper arm drive circuit 8 and lower arm drive circuit 9 in order to turn on as desired the transistors Ua, Va, and Wa of the upper arm and the transistors Xa, Ya, and Za of the lower arm of the first inverter circuit 4 on the basis of the position detecting signals so as to rotate the first brushless motor 3, respectively. The microcomputer 7 outputs a chopping signal shown in (j) in Fig. 12 to the chopping circuit 10. The chopping circuit 10 chops a power source of the upper arm drive circuit 8 on the basis of the inputted chopping signal in order to chop as desired an output signal of, for example, the upper arm drive circuit 8 on the basis of the input chopping signal. Thus, the PWM signals Ual, Val, and Wal in which the ON portions of input drive signals shown in (k) to (m) in Fig. 12 were chopped are outputted from the upper arm drive circuit 8 to the transistors Ua, Va, and Wa of the upper arm of the inverter circuit 4. Signals Xal, Yal, and Zal shown in (n) to (p) in Fig. 12 are outputted from the lower arm drive circuit 9 to the transistors Xa, Ya, and Za of a lower arm of the inverter circuit 4 on the basis of the input drive signals. The transistors Ua, Va, Wa, Xa, Ya, and Za of the upper and lower arms of the first inverter circuit 4 are turned on as desired by output signals of the upper arm drive circuit 8 and lower arm drive circuit 9. The connections between the positive and negative terminals of the inverter circuit 4 and the 3-phase windings al, bl, and cl of the first brushless motor 3 are switched. Thus, the DC voltage from the converter circuit 2 is converted to the AC voltage and is applied to the 3-phase windings a1, b1, and c1 of the first brushless motor 3. At the same time, the transistors Ua, Va, and Wa of the upper arm are choppingly driven by the output signal of the upper arm drive circuit 8 when they are turned on. Therefore, the chopped AC voltages shown in (q) to (s) in Fig. 12 are applied to the 3-phase windings al, bl, and cl of the first brushless motor 3. In the microcomputer 7, the on/off ratio of the chopping signal which is supplied to the chopping circuit 10 is made variable in order to set the rotational speed of the first brushless motor 3 to a predetermined rotational speed. The on/off ratio of the chopping of AC voltages which are applied to the 3-phase windings al, bl, and cl of the first brushless motor 3 is made variable, thereby varying the applied voltages and controlling the rotation of the first brushless motor 3. On the other hand, in the switching power circuit 11, the commercial AC power 1 is converted to the DC power by a rectifying circuit lla and a smoothing capacitor 11b and a predetermined DC voltage is generated. The DC voltage is switched and converted to the variable DC voltage by a transformer 11c, the transistor 11d, a diode lle, and a smoothing capacitor 11f. The variable DC voltage is supplied to the second inverter circuit 13 comprising the six transistors Ub, Vb, Wb, Xb, Yb, and Zb. The second brushless motor 12 has therein the position detecting sensor (Hall elements) 12a. The Hall elements 12a detect the position of a rotor of the second brushless motor 12 and generates position detecting signals shown in (a) to (c) in Fig. 13. The brushless motor control circuit 14 which receives the position detecting signals from the Hall elements 12a is constructed by, for example, an exclusive use IC for brushless motor control and the like. The brushless motor control circuit 14 outputs drive signals Ub1, Vb1, Wb1, Xb1, Yb1, and Zb1 shown in (d) to (i) in Fig. 13 to the transistors Ub, Vb, Wb, Xb, Yb, and Zb of the second inverter circuit 13 on the basis of the inputted position detecting signals so as to rotate the second brushless motor 12. The transistors of the second inverter circuit 13 are turned on as desired by those drive signals. The variable DC voltage from the switching power circuit 11 which is inputted to the inverter circuit 13 is converted to the AC voltages shown in (j) to (ℓ) in Fig. 13 and applied to 3-phase windings a2, b2, and c2 of the second brushless motor 12. Further, the microcomputer 7 generates a rotational speed command signal for the second brushless motor 12. The brushless motor control circuit 14 which receives the rotational speed command signal generates a switching signal to switching control the transistor 11d of the switching power circuit 11 [shown in (m) in Fig. 13]. The brushless motor control circuit 14 varies the on/off ratio of the above switching signal on the basis of the inputted rotational speed command signal and varies the DC voltage that is generated by the switching power circuit 11. The varied DC voltage is converted to the variable AC voltage by the inverter circuit 13 and this AC voltage applied to the 3-phase windings a2, b2, and c2 of the second brushless motor 12. Since the AC voltage which is applied to the 3-phase windings a2, b2, and c2 is made variable, the second brushless motor 12 is variable-speed controlled. In such a conventional control method of the air conditioner as mentioned above, however, three control means such as converter control circuit 5, microcomputer 7, and brushless motor control circuit 14 are necessary in order to improve the input power factor, to control the converter circuit 2 for reducing the harmonics current, and to control the rotations of the motors (first and second brushless motors 3 and 12) to drive the compressor and blower which are necessary for the air conditioner. In order to drive the second brushless motor 12, the switching power circuit 11 for varying the DC voltage and outputting is needed. Further, the control circuit and the power supply circuit of the air conditioner are complicated. The number of parts is large. The reliability is deteriorated. Such three control means become a factor of an increase in costs and size of the air conditioner. In the rotation control of the second brushless motor 12, the on/off ratio of the switching signal is determined by only the rotational speed command signal from the microcomputer 7. The value of the DC voltage that is outputted from the switching power circuit 11 is decided. Therefore, the rotational speed of the second brushless motor 12 fluctuates in association with a fluctuation of the load. The actual rotational speed doesn't coincide with the rotational speed decided by the rotational speed command signal. Namely, there is a problem such that the second brushless motor 12 doesn't rotate in accordance with the rotational speed command signal. SUMMARY OF THE INVENTION It is an object of the invention to provide a control method and apparatus of an air conditioner, in which a converter, a compressor, and a blower of the air conditioner can be controlled by a single microcomputer of the air conditioner. The invention provides for a method as defined in claim 1 and an apparatus as defined in claim 4. A control apparatus according to an embodiment of the invention comprises: converter means for converting an AC power to DC power and for converting an input AC current waveform to a sine wave of the same phase as that of an input voltage by at least switching means; a plurality of motors for driving a compressor and a blower; a plurality of inverters for converting the converted DC power to the AC power and for supplying it to the motors; and a microcomputer for controlling at least the compressor and blower of the air conditioner, wherein the control apparatus further comprises: the plurality of inverters which are connected in parallel and receive an output DC power from the converter; converter control means for outputting a control signal to control the switching means in accordance with at least the input AC current from the microcomputer and the output DC voltage of the converter; and inverter control means for outputting a control signal to control the plurality of inverters. "At least" is stated before the phrase "switching means" for the reason that in the present invention, the microcomputer outputs control signals for controlling the switching means (IGBT), and also in the prior art, the converter control circuit outputs control signals for controlling the switching means (IGBT) so that the input AC current from the AC power has a sine wave of the same phase as that of the input AC voltage. With such a construction, the microcomputer executes input/output operations from/to input/output circuits which are necessary for the air conditioner, thereby controlling the air conditioner. At the same time, the microcomputer generates a PWM signal to turn on-off the switching means of the converter in a manner such that the input alternating current from the commercially available AC power is set to a sine wave having the same phase as that of the input AC voltage and the input power factor from the commercially available AC power is improved. Further, simultaneously with the above operation, the microcomputer also generates the PWM signal for on/off controlling the switching means of each inverter in order to inverter control each of the motors (brushless motors or induction motors) to drive the compressor and blower which are necessary for the air conditioner. Therefore, the control of the air conditioner, the control of the switching means of the converter, and the inverter control of the motors for the compressor and blower which are necessary for the air conditioner are executed by the microcomputer as single control means. Since the output DC voltage of the converter is applied to each motor, each motor is driven by the single power circuit. Thus, the number of parts can be reduced, the reliability can be improved, and the costs and size of the air conditioner can be reduced. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a schematic block diagram showing an embodiment of a control apparatus of an air conditioner of the invention; Fig. 2 is a schematic timing chart for explaining the operation and control method of the control apparatus shown in Fig. 1; Fig. 3 is a schematic timing chart for explaining the operation and control method of the control apparatus shown in Fig. 1; Fig. 4 is a schematic block diagram of a control apparatus of an air conditioner showing a modified embodiment of the invention; Fig. 5 is a schematic timing chart for explaining the operation and control method of the control apparatus shown in Fig. 4 ; Fig. 6 is a schematic constructional diagram of a microcomputer which is used in the control apparatus of the air conditioner shown in Fig. 1; Fig. 7 is a schematic timing chart for explaining the operation of the microcomputer shown in Fig. 6; Fig. 8 is a schematic constructional diagram of a different microcomputer which is used in the control apparatus of the air conditioner shown in Fig. 1; Fig. 9 is a schematic constructional diagram of a microcomputer which is used in the control apparatus of the air conditioner shown in Fig. 4; Fig. 10 is a schematic block diagram of a control apparatus of a conventional air conditioner; Fig. 11 is a timing chart for explaining the operation of the control apparatus shown in Fig. 10; Fig. 12 is a timing chart for explaining the operation of the control apparatus shown in Fig. 10; and Fig. 13 is a timing chart for explaining the operation of the control apparatus shown in Fig. 10. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS A control method and an apparatus of an air conditioner according to the invention will now be described in detail with reference to the drawings. In the diagrams, the same and corresponding portions as those in Fig. 10 are designated by the same reference numerals and their overlapped descriptions are omitted. In Fig. 1, a control apparatus 32 of the air conditioner comprises: a current sensor 20 and a current detecting circuit 21 for detecting an input alternating current of the converter circuit 2; a voltage detecting circuit 22 to detect the output DC voltage of the converter circuit 2; a first position detecting circuit 23 having the same construction as that of the position detecting circuit 6 shown in Fig. 10, for outputting position detecting signals of the rotor of the brushless motor 3 to drive a compressor 33; a second position detecting circuit 24 for outputting position detecting signals of the rotor of the brushless motor 12 to drive a blower 34; and a microcomputer 25 for performing input/output operations which are necessary to control the air conditioner, for inputting a current detecting signal from the current detecting circuit 21, a voltage detecting signal from the voltage detecting circuit 22, the position detecting signals from the first position detecting circuit 23, and the position detecting signals from the second position detecting circuit 24, for turning on or off as desired the IGBT (transistor) 2a included in the converter circuit 2 for outputting a control signal [an inverter control signal (PWM signal)] in which the on ratio is varied, and for outputting: control signals (including the PWM signal) for respectively controlling the first and second inverter circuits 4 and 13 in addition to the functions (function to output the PWM signal, and the like) of the microcomputer 7 shown in Fig. 10; apparatus 32 further comprises first and second driving circuits 26 and 27 for respectively driving the plurality of transistors of the first and second inverter circuits 4 and 13 by the control signals from the microcomputer 25, and a third driving circuit 28 to turn on/off the IGHT 2a by the PWM signal from the microcomputer 25. The operation of the control apparatus 32 of the air conditioner will now be described. The microcomputer 25 controls an outdoor apparatus and generates the PWM signal for switching as desired the IGBT 2a of the converter circuit 2 to the third driving circuit 28 in accordance with the detecting signals from the current detecting circuit 21 and voltage detecting circuit 22. The microcomputer 25 also inputs the position detecting signals of the rotor of the first brushless motor 3 for the compressor 33 from the first position detecting circuit 23 and generates control signals for controlling the six transistors Ua, Va, Wa, Xa, Ya, and Za of the first inverter circuit 4. At the same time, the microcomputer 25 inputs the position detecting signals of the rotor of the second brushless motor 12 for the blower 34 from the second position detecting circuit 24 and generates control signals for controlling the six transistors Ub, Vb, Wb, Xb, Yb, and Zb of the second inverter circuit 13. The current detecting circuit 21 comprises, for example, a rectifying diode and a resistor circuit and converts the input alternating current waveform detected by the current sensor 20 to a level (voltage value) which can be inputted to the microcomputer 25. The voltage detecting circuit 22 comprises, for example: a voltage dividing resistor circuit for dropping the output DC voltage of the converter circuit 2; and a photocoupler circuit for isolating the voltage dropped analog value and converting it to digital values (H, L) and supplying them to the microcomputer 25. The voltage dividing ratio of the voltage dividing resistor circuit of the voltage detecting circuit 22 is set in a manner such that when the output DC voltage of the converter circuit 2 is equal to or less than a predetermined value [for example, 300 V shown in (a) in Fig. 2], the output of the photocoupler circuit is set to the H level, and, when the output DC voltage exceeds the predetermined value, the output of the photocoupler circuit is set to the L level. Thus, the voltage detecting signal from the voltage detecting circuit 22 is set to the H or L level. The H or L level signal is supplied to the microcomputer 25. The voltage detecting circuit 22 can also output an analog value according to the difference between the output DC voltage of the converter circuit 2 and a predetermined value.In this case, it is sufficient that the analog signal from the voltage detecting circuit 22 is inputted to an A/D conversion input port of the microcomputer 25. The control method of the converter circuit 2 used in the control apparatus 32 of the air conditioner will now be described with reference to a timing chart of Fig. 2. First, the microcomputer 25 calculates a current command ISn shown in (c) in Fig. 2 on the basis of data [IMn shown in (b) in Fig. 2; n is an integer] which has previously been stored in an internal memory, and of the detecting signal (H or L level) of the output DC voltage of the converter circuit 2 which was inputted. The memory data IMn is a sine wave data (fundamental data) of the half period of the input alternating current. As a calculating method of the current command ISn, the voltage detecting signal from the voltage detecting circuit 22 is detected every predetermined time [for instance, zero-cross point of the input AC waveform shown in (d) in Fig. 2] and, when it is at the H level (300 V or less), a predetermined ratio of the memory data is added to the memory data IMn, thereby incrementing the current command ISn. Thus, until the voltage detecting signal is set to the L level (exceeding 300 V), the predetermined ratio of the memory data is added to the memory data IMn, thereby increasing the current command ISn. Then, when the voltage detecting signal changes to the L level (exceeding 300 V), the predetermined ratio of the memory data is subtracted from the memory data IMn, thereby decrementing the current command ISn. Until the voltage detecting signal is again set to the H level (300 V or less), the predetermined ratio of the memory data is continued to be subtracted, thereby decreasing the current command ISn. On the basis of the current command ISn calculated in this manner, the IGBT 2a of the converter circuit 2 is turned on or off as desired, thereby setting the output DC voltage of the converter circuit 2 to the predetermined value (300 V). The current detecting circuit 21 detects the input alternating current and supplies the current detecting signal to the microcomputer 25. The microcomputer 25 detects a current value IRn shown in (e) in Fig. 2 by the current detecting signal at times tn (t0 to t9) of every predetermined time T from a zero-cross point (t0). The zero-cross point (t0) is detected by a detecting signal from a zero-cross detecting circuit which is used for judgment of the frequency of the input alternating current or the like as one of the existing input/output circuits of the outdoor apparatus. The current command ISn [shown in (c) in Fig. 2] at time tn is subsequently compared with the detecting current IRn [shown in (e) in Fig. 2]. When ISn > IRn, the ON time Dn of the PWM signal to control the IGBT 2a of the converter circuit 2 is increased by only a predetermined value. When ISn < IRn, the ON time Dn of the PWM signal to control the IGBT 2a of the converter circuit 2 is decreased by only the predetermined value [refer to (f) in Fig. 2]. Thus, the input alternating current from the commercial AC power 1 can be controlled to the sine wave having the same phase as that of the input AC voltage as shown in (d) in Fig. 2. And in this instance, as already has been described above, also the output DC voltage of the converter circuit 2 is controlled to the predetermined value. On the other hand, as will be obviously understood from Fig. 1, the first and second inverter circuits 4 and 13 are connected in parallel with the output of the converter circuit 2. The first inverter circuit 4 drives the first brushless motor 3 for the compressor 33. The second inverter circuit 13 drives the second brushless motor 12 for the blower 34. The first and second brushless motors 3 and 12 are 3-phase motors and are controlled by the single microcomputer 25 which controls both the outdoor apparatus and the IGBT 2a of the converter circuit 2. The second position detecting circuit 24 comprises, for example, comparator means and amplifier means; it inputs signals from three Hall elements 12a provided in the second brushless motor 12 and supplies the position detecting signals of the rotor of the second brushless motor 12 to the microcomputer 25. The second inverter circuit 13 is constructed by: an upper arm comprising the three transistors Ub, Vb, and Wb for switching the connections between a positive terminal of the converter circuit 2 and the 3-phase windings a2, b2, and c2 of the second brushless motor 12; and a lower arm comprising the three transistors Xb, Yb, and Zb for switching the connections between the 3-phase windings a2, b2, and c2 and a negative terminal of the converter circuit 2. In Fig. 1, the first driving circuit 26 has a construction such that the upper arm drive circuit 8 and lower arm drive circuit 9 shown in Fig. 10 are unified. The second driving circuit 27 has a construction similar to that of the driving circuit 26. A control method will now be described with reference to a timing chart of Fig. 3. First, it is assumed that the microcomputer 25 controls the compressor 33 and blower 34 of the outdoor apparatus in accordance with commands or the like from a control apparatus of an indoor apparatus. The signals [shown in (a) to (c) in Fig. 3] from the Hall elements 12a in the second brushless motor 12 are supplied to the second position detecting circuit 24. The second position detecting circuit 24 outputs position detecting signals shown in (d) to (f) in Fig. 3 to the microcomputer 25. The microcomputer 25 turns on as desired the transistors Ub, Vb, Wb, Xb, Yb, and Zb of the second inverter circuit 13 on the basis of the input position detecting signals so as to rotate the second brushless motor 12, switches the connections between the positive and negative terminals of the converter circuit 12 and the 3-phase windings a2, b2, and c2 of the second brushless motor 12, converts the DC voltages from the converter circuit 2 to the AC voltages, applies the AC voltages to the 3-phase windings a2, b2, and c2, and generates control signals U2, V2, W2, X2, Y2, and Z2 to rotate the second brushless motor 12. In this instance, the microcomputer 25 sets the ON portions of the control signals for turning on as desired the transistors Ub, Vb, and Wb of at least one of the upper and lower arms, for instance, the upper arm of the second inverter circuit 13 among the generated control signals to chopping signals of a predetermined on/off ratio for turning on/off the transistors Ub, Vb, and Wb of the upper arm by a frequency higher than the frequency of the control signals in the microcomputer 25. Thus, the control signals U2, V2, and W2 [shown in (g) to (i) in Fig. 3] using the ON portions as chopping signals, and the other control signals X2, Y2, and Z2 [shown in (j) to (ℓ) in Fig. 3] are generated from the microcomputer 25. The generated control signals U2, V2, W2, X2, Y2, and Z2 are supplied to the second inverter circuit 13 through the second driving circuit 27. The transistors Ub, Vb, Wb, Xb, Yb, and Zb of the second inverter circuit 13 are turned on as desired. At the time when the transistors Ub, Vb, and Wb of the upper arm are principally ON, they are in fact turned on/off by the chopping signals of the control signals. The DC voltages from the converter circuit 2 are converted to the AC voltages and are chopped.The AC voltages are set to predetermined voltages.AC voltages shown in (m) to (o) in Fig. 3 are applied to the 3-phase windings a2, b2, and c2 of the second brushless motor 12, so that the second brushless motor 12 is rotation-controlled. With respect to the first brushless motor 3 as well, the rotation is controlled by a method similar to that mentioned above by the microcomputer 25. The microcomputer 25 inputs the position detecting signals which are outputted from the first position detecting circuit 23 and generates control signals U1, V1, W1, X1, Y1, and Z1 to turn on as desired the transistors Ua, Va, Wa, Xa, Ya, and Za of the first inverter circuit 4 on the basis of the position detecting signals so as to rotate the first brushless motor 3. Among the control signals U1, V1, W1, X1, Y1, and Z1, the ON portions of the control signals U1, V1, and W1 to turn on as desired the transistors Ua, Va, and Wa, of at least one of the upper arm and lower arm, for example, the upper arm of the first inverter circuit 4 are set to be chopping signals of a predetermined on/off ratio to turn on/off the transistors Ua, Va, and Wa by a frequency higher than the frequency of the control signals in the microcomputer 25. The microcomputer 25 generates the control signals U1, V1, W1, X1, Y1, and Z1 including the drive signals serving as chopping signals. The generated control signals U1, V1, W1, X1, Y1, and Z1 are supplied to the first inverter circuit 4 through the first driving circuit 26. The transistors Ua, Va, Wa, Xa, Ya, and Za of the first inverter circuit 4 are turned on as desired and, at the same time, the transistors Ua, Va, and Wa are chopped at the time of turn-on thereof. Thus, the DC voltage from the converter circuit 2 is converted to the AC voltages and the chopped AC voltages are applied to the 3-phase windings a1, b1, and c1 of the first brushless motor 3, thereby rotation-controlling the first brushless motor 3. The control signals U1, V1, W1, X1, Y1, and Z1 are the same as the signals Ua1, Va1, Wa1, Xa1, Ya1, and Za1 shown in Fig. 12. The rotation control in the second brushless motor 12 will now be described in detail. The microcomputer 25 calculates the rotational speed of the second brushless motor 12 on the basis of the position detecting signals [shown in (d) to (f) in Fig. 3] inputted through an input port. As a calculating method of the rotational speed, for instance, a time interval between leading edges or trailing edges of the three inputted position detecting signals [shown in (d) to (f) in Fig. 3] is measured thereby calculating the rotational speed. The above calculated rotational speed is compared with a predetermined rotational speed of the second brushless motor 12. When the calculated rotational speed is smaller than the predetermined rotational speed, the rotational speed of the second brushless motor 12 is set to the predetermined rotational speed. For this purpose, the ON times of the chopping signals of the drive signals U2, V2, and W2 of the transistors Ub, Vb, and Wb of the upper arm constructing the second inverter circuit 13 are increased (namely, the OFF times are decreased; on/off ratio is varied). Thus, the resulting AC voltages which are applied to the 3-phase windings a2, b2, and c2 of the second brushless motor 12 are raised and the rotational speed of the second brushless motor 12 is increased. When the calculated rotational speed is larger than the predetermined rotational speed, in order to set the rotational speed of the second brushless motor 12 to the predetermined rotational speed, the ON times of the chopping signals of the control signals U2, V2, and W2 of the transistors Ub, Vb, and Wb of the upper arm are decreased (namely, OFF times are increased; on/off ratio is varied). Thus, the resulting AC voltages which are applied to the 3-phase windings a2, b2, and c2 of the second brushless motor 12 are dropped and the rotational speed of the second brushless motor 12 is reduced. By repeating the above operations, the rotational speed of the second brushless motor 12 is variably controlled and the motor 12 is constantly rotated and controlled at a predetermined rotational speed. With respect to the first brushless motor 3 as well, a rotation control similar to the rotation control of the second brushless motor 12 is executed. Therefore, the first and second brushless motors 3 and 12 are constantly rotated and controlled at predetermined respective rotational speeds by the microcomputer. Fig. 4 is a schematic circuit diagram of the control apparatus 32 of the air conditioner showing a modified embodiment of the invention. In the diagram, the same and corresponding portions as those in Fig. 1 are designated by the same reference numerals and their overlapped descriptions are omitted. In the embodiment, an induction motor 30 is used in place of the first brushless motor 3 for the compressor 33. The converter circuit 2 and the second brushless motor 12 for the blower 34 are similar to those shown in the foregoing embodiment. In Fig. 4, the control apparatus of the air conditioner has a microcomputer 31 which has the functions of the microcomputer 25 shown in Fig. 1 and controls the rotation of the induction motor 30 for the compressor 33. First, when the rotation of the induction motor 30 is controlled, the microcomputer 31 compares a modulation wave shown in (a) in Fig. 5 with fundamental waves U, V, and W every half period Tf4 and obtains intersection points between the modulation wave and the fundamental waves U, V, and W, respectively. On the basis of the intersection points obtained, times Tu4, Tv4, and Tw4 up to the intersection points shown in (a) in Fig. 5 are obtained. On the basis of the times Tu4, Tv4, and Tw4 obtained, control signals (PWM signals) U4, X4, V4, Y4, W4, and Z4 (X4, Y4, and Z4 are the signals obtained by inverting U4, V4, and W4) are generated and outputted [shown in (b) to (g) in Fig. 5]. The first driving circuit 26 which received the first PWM signals U4, X4, V4, Y4, W4, and Z4 from the microcomputer 31 turns on/off the six transistors Ua, Xa, Va, Ya, Wa, and Za constructing the first inverter circuit 4 on the basis of the drive signals U4, X4, V4, Y4, W4, and Z4. As mentioned above, since the transistors Ua, Xa, Va, Ya, Wa, and Za of the first inverter circuit 4 are on/off controlled, the output DC voltage from the converter circuit 2 is converted to the 3-phase alternating currents. The 3-phase alternating currents are supplied to the 3-phase windings a3, b3, and c3 of the induction motor 30 [shown in (h) in Fig. 5], so that the induction motor 30 is rotated. In this instance, to set the induction motor 30 to a predetermined rotational speed, the microcomputer 31 sets the fundamental waves U, V, and W to predetermined amplitudes and predetermined frequencies in accordance with the predetermined rotational speed of the induction motor 30, thereby varying the intersection points between the modulation wave and the fundamental waves U, V, and W and varying Tu4, Tv4, and Tw4 mentioned above.Thus, pulse widths (on/off timings) of the control signals (PWM signals) U4, X4, V4, Y4, W4, and Z4 are varied by such variation and are outputted from the microcomputer 31. The 3-phase alternating currents to be supplied from the first inverter circuit 4 to the induction motor 30 are subsequently set to predetermined voltages and predetermined frequencies. The induction motor 30 is rotated at a predetermined rotational speed. The microcomputer which is used in the control apparatus of the invention will now be specifically explained. The whole construction of the first control apparatus is shown in Fig. 1. Fig. 6 is a specific constructional block diagram of signal generating means in the microcomputer 25 shown in Fig. 1. In Fig. 6, the microcomputer 25 has first to third signal generating means 40, 41, and 42. The third signal generating means 42 generates the third PWM signal to control the IGBT 2a of the converter circuit 2. The first and second signal generating means 40 and 41 respectively generate the first and second control signals to control the first and second inverter circuits 4 and 13. The first and second control signals and the third PWM signal are outputted from the microcomputer 25. The third signal generating means 42 will now be described. The third signal generating means 42 generates the third PWM signal shown in (a) in Fig. 7. In this instance, the microcomputer 25 sets a period Tf3 and an ON time Ton3 [shown in (a) in Fig. 7] of the third PWM signal into an internal memory 42a and resets a timer counter 42b and starts. At the same time, the microcomputer 25 sets the third PWM signal that is outputted from comparator means 42c to the H level (on). The comparator means 42c compares a count value of the timer counter 42b with Ton3 in the memory 42a.When they coincide, an output signal (third PWM signal) of the comparator means 42c is set to the L level (off). After that, when Tf3 in the memory 42a coincides with the count value of the timer counter 42b, the timer counter 42b is reset and is restarted. At the same time, the third PWM signal that is outputted from the comparator means 42c is set to the H level (on). For such a period of time, the value of Ton3 in the memory 42a is rewritten to the ON time data of the next pulse by the microcomputer 25, so that the pulse width of the third PWM signal which is outputted changes. By repeating the foregoing processes, the third PWM signal shown in (a) in Fig. 7 is generated and is outputted from the microcomputer 25. First and second control signal generating means 40e and 41e of the first and second signal generating means 40 and 41 receive the first and second position detecting signals [shown in (b) to (d) in Fig. 7] of the first and second brushless motors 3 and 12, respectively. On the basis of the position detecting signals, the control signals U1, V1, W1, X1, Y1, and Z1 and control signals U2, V2, W2, X2, Y2, and Z2 shown in (e) to (j) in Fig. 7 for turning on as desired the transistors Ua, Va, Wa, Xa, Ya, Za, Ub, Vb, Wb, Xb, Yb, and Zb of the first and second inverters 4 and 13 are generated so as to rotate the first and second brushless motors 3 and 12, respectively. In memories 40a and 41a, timer counters 40b and 41b, and comparator means 40c and 41c, a first PWM reference signal and a second PWM reference signal [shown in (k) in Fig. 7] of predetermined on/off ratios are generated at frequencies higher than the frequency of each of the generated control signals, respectively. In this instance, periods Tfl and Tf2 [shown in (k) in Fig. 7] of the first and second PWM reference signals are set into the memories 40a and 41a. Further, predetermined ON times Tonl and Ton2 of the first and second PWM reference signals are set into the memories 40a and 41a, respectively. The timer counters 40b and 41b are reset and started and, at the same time, the first and second PWM reference signals are set to the H level (on). In the comparator means 40c and 41c, count values of the timer counters 40b and 41b are compared with the values of the ON times Tonl and Ton2 of the first and second PWM reference signals in the memories 40a and 41a, respectively. When they coincide, the corresponding PWM reference signal is set to the L level (off). After that, count values of the timer counters 40b and 41b are compared with values of the periods Tfl and Tf2 of the first and second PWM reference signals in the memories 40a and 41a, respectively. When they coincide, the timer counters 40b and 41b are reset and restarted. Simultaneously with it, the first and second PWM reference signals are set to the H level (on). After that, by repeating processes similar to those mentioned above, the first and second PWM reference signals are generated [shown in (k) in Fig. 7]. First and second PWM signal generating means 40d and 41d input the generated control signals and also input the generated first and second PWM reference signals. Among the inputted control signals, the ON portions of the control signals U1, V1, Wl, U2, V2, and W2 to turn on as desired the transistors Ua,Va,Wa,Ub,Vb,and Wb of at least one of the upper and lower arms, in the example, the upper arm of the first and second inverter circuits 4 and 13 are set to the PWM signals by the first and second PWM reference signals. In the first and second PWM signal generating means 40d and 41d, the ANDs or ORs between the control signals U1, V1, W1, U2, V2, and W2 as PWM signals and the first and second PWM reference signals, in the example, the ANDs are obtained. In case of the second PWM signal generating means 41d, as shown in (ℓ) to (n) in Fig. 7, the second control signals U2, V2, and W2 are set to the second PWM reference signal [shown in (k) in Fig. 7] only when the output signals are at the H level. Thus, the ON portions of the control signals of the upper arms of the first and second inverter circuits 4 and 13 are set to the first and second PWM reference signals, respectively. The first and second PWM signals U1, V1, and W1 and U2, V2, and W2 shown in (ℓ) to (n) in Fig. 7 in which the ON portions are set to the first and second PWM reference signals and the other first and second control signals X1, Y1, and Z1 and X2, Y2, and Z2 shown in (o) to (q) in Fig. 7 are generated by the first and second PWM signal generating means 40d and 41d, respectively. The twelve first and second output control signals generated are outputted from the microcomputer 25. The first and second control signal generating means 40e and 41e generate the control signals to the first and second PWM signal generating means 40d and 41d on the basis of the first and second position detecting signals, respectively. The microcomputer 25 varies as desired the ON times Ton1 and Ton2 of the first and second PWM reference signals which are set into the memories 40a and 41a, thereby constantly rotation-controlling the first and second brushless motors 3 and 12 at predetermined rotational speeds, respectively. In the above embodiment, the periods Tf1, Tf2, and Tf3 of the first to third PWM signals have individually been set. However, two or three of those periods can be also set to a common period. In this case, the memories, timer counters, and comparator means can be also commonly constructed. Fig. 8 shows an example in the case where the above three periods are commonly set. As will be obviously understood from Fig. 8, first, second, and third signal generating means 50 of the microcomputer 25 comprise: a memory 50a for setting the period Tf of the PWM signal, ON time Tonl of the first PWM signal, ON time Ton2 of the second PWM signal, and ON time Ton3 of the third PWM signal; a timer counter 50b; comparator means 50c; first and second PWM signal generating means 50d and 50e; and first and second control signal generating means 50f and 50g. That is, the memory 50a corresponds to the memory shown in Fig. 6. The timer counter 50b corresponds to the timer counter shown in Fig. 6. The comparator means 50c corresponds to the comparator means shown in Fig. 6. The first and second PWM signal generating means 50d and 50e correspond to the first and second PWM signal generating means shown in Fig. 6. The first and second control signal generating means 50f and 50g correspond to the first and second control signal generating means shown in Fig. 6. Since the operations of the signal generating means in such a construction are also similar to those mentioned above, their descriptions are omitted here. Fig. 9 is a schematic block diagram showing a construction of the signal generating means in the microcomputer 31 shown in Fig. 4. In the example, a first signal generating means 60 is provided to control the induction motor 30 for the compressor 33 shown in Fig. 4. The periods of the second and third PWM signals are set to the same period. Second and third signal generating means 61 for generating the second and third PWM signals are unified. The second and third signal generating means 61 have a construction similar to that of the first, second, and third signal generating means shown in Fig. 8. The whole construction of this second control apparatus of the air conditioner is shown in the schematic block diagram of Fig. 4. The operations are shown in the timing charts of Fig. 5. The first signal generating means 60 of the microcomputer 31 will be first described. In the half period Tf4 of the modulation wave, intersection points between the modulation wave and the fundamental waves U, V, and W are obtained [refer to (a) in Fig. 5] and the times Tu4, Tv4, and Tw4 up to the intersection points are obtained [refer to (b), (d), and (f) in Fig. 5]. The microcomputer 31 sets the half period Tf4 of the modulation wave into a memory 60a and also sets the obtained values Tu4, Tv4, and Tw4 into the memory 60a. A timer counter 60b is reset and started.At the same time, three signals U4, V4, and W4 [refer to (b), (d), and (f) in Fig. 5] which are outputted from a comparator means 60c are set to the L level. The comparator means 60c compares a count value of the timer counter 60b with the values Tu4, Tv4, and Tw4 in the memory 60a, respectively. When they coincide, each output signal is inverted. When the count value of the timer counter 60b coincides with the value in the memory 60a as a half period Tf4 of the modulation wave, the comparator means 60c resets the timer counter 60b. For such a period of time, the intersection points between the modulation wave in the next half period of the modulation wave and the fundamental waves U, V, and W are obtained in the microcomputer 31. From the intersection points, the new values Tu4, Tv4, and Tw4 are obtained and are again set into the memory 60a simultaneously with the reset of the timer counter 60b. The timer counter 60b is restarted. By repeating the above processes, the PWM signals U4, V4, and W4 shown in Fig. 5 are outputted from the comparator means 60c. The above three PWM signals U4, V4, and W4 are respectively inverted by inversion means 60d, 60e, and 60f and become the PWM signals X4, Y4, and Z4 shown in (c), (e), and (g) in Fig. 5. The inverted signals X4, Y4, and Z4 and non-inversion signals U4, V4, and W4 are inputted to dead time generating means 60g. The dead time generating means 60g is delay means. In order to prevent that the two transistors (Ua and Xa; Va and Ya; Wa and Za) of the same phase of the first inverter circuit 4 are simultaneously turned on and the power supply is shortcircuited, for instance, the leading edges of the inputted signals U4, V4, W4, X4, Y4, and Z4 are delayed by a predetermined time, thereby preventing that the two transistors of the same phase are simultaneously set to the H level (on). As mentioned above, six PWM signals U4, V4, W4, X4, Y4, and Z4 as first control signals are generated from the first signal generating means 60 and are outputted from the microcomputer 31. At the same time, in order to set the induction motor 30 to a predetermined rotational speed, the microcomputer 31 varies the fundamental waves U, V, and W to predetermined amplitudes and predetermined frequencies in accordance with the predetermined rotational speed, thereby varying the intersection points between the modulation wave and the fundamental waves. Thus, the values Tu4, Tv4, and Tw4 which are set into the memory 60a are varied, the pulse widths (on/off timings) of the six PWM signals are varied and outputted, and the rotational speed of the induction motor 30 is varied, thereby rotating the induction motor at a predetermined rotational speed. The half period Tf4 of the modulation wave which is set into the memory 60a can be also varied as necessary. Since the second and third signal generating means 61 have already been described in Fig. 8, the description of the operations are omitted here. In this case, in Fig. 9, the memory 61a corresponds to the memory 50a shown in Fig. 8, the timer counter 61b corresponds to the timer counter 50b shown in Fig. 8, the comparator means 61c corresponds to the comparator means 50c shown in Fig. 8, the second PWM signal generating means 61d corresponds to the second PWM signal generating means 50e shown in Fig. 8, and the second control signal generating means 61e corresponds to the second control signal generating means 50g shown in Fig. 8.

Claims: Method of controlling motors (3, 12, 30) of an air conditioner, the motors serving for driving a compressor (33) and a blower (34), the air conditioner further comprising a converter (2) for converting an AC power (1) to a DC power, the converter being controlled by at least switching means (2a), a plurality of inverters (4, 13) for converting said converted DC power to AC powers and supplying to said motors, and a microcomputer (25, 31) for controlling at least the compressor and blower of said air conditioner, said plurality of inverters being connected in parallel to the DC output of said converter, the method comprising the steps of outputting from said microcomputer a control signal for controlling said switching means (2a) in accordance with at least the input alternating current and the output DC voltage of said converter (2) so that the current supplied by the AC power (1) to the converter is in phase with the voltage of the AC power; and control signals for controlling said plurality of inverters (4, 13). Method according to claim 1, characterized in that at least part of the control signals are chopped on/off signals having a varying duty ratio. Method according to claim 1 or 2, characterized in that at least part of the control signals are pulse-width modulation signals (PWM signals) (Fig. 2(f), Fig. 3(g)-(i)). Apparatus for controlling motors (3, 12, 30) of an air conditioner, the motors serving for driving a compressor (33) and a blower (34), the apparatus comprising a converter (2) for converting an AC power (1) to a DC power, the converter being controlled by at least switching means (2a), a plurality of inverters (4, 13) for converting said converted DC power to AC powers and supplying to said motors, and a microcomputer (25, 31) for controlling at least the compressor and blower of said air conditioner, said plurality of inverters being connected in parallel to the DC output of said converter, said microcomputer outputting a control signal for controlling said switching means (2a) in accordance with at least the input alternating current and the output DC voltage of said converter (2) so that the current supplied by the AC power (1) to the converter is in phase with the voltage of the AC power; and control signals for controlling said plurality of inverters (4, 13). Apparatus according to claim 4, characterized in that it further comprises said plurality of motors to drive said compressor and blower which are brushless motors. Apparatus according to claim 5, characterized in that the inverter control means (25, 26, 27) output the control signals to control said plurality of inverters (4, 12) from said microcomputer (31) on the basis of position detecting signals (Fig. 3(d)-(f), Fig. 7(b)-(d)) of rotors of said plurality of brushless motors (3, 12). Apparatus according to claim 4, characterized in that among said plurality of motors to drive said compressor (33) and blower (34), at least one of the motors is an induction motor (30) and the other motors are brushless motors. Apparatus according to claim 7, characterized in that the inverter control means (26, 27, 31) outputs the control signals to control said inverters (12) for supplying AC powers to said brushless motors (12) from said microcomputer (31) on the basis of position detecting signals of rotors of said brushless motors (12) and outputs a control signal (Fig. 5(b)-(g)) to control the inverter (4) for supplying the AC power (Fig. 5(h)) to said induction motor (30).

Inventors: OGAWA YOSHIO, TODA KOICHI, OGAWA, YOSHIO, TODA, KOICHI, OGAWA, YOSHIO, C/O FUJITSU GENERAL LIMITED, Toda, Koichi, c/o Fujitsu General Limited
Applicants: FUJITSU GENERAL LTD, FUJITSU GENERAL LIMITED
Application year: 1995
Main classification: F24F11
IPC codes: F24F11, H02P6, F25B49, H02P5, F25B1, H02M7