Method and apparatus for automatic frequency control

Abstract: An automatic frequency control apparatus used in an MPSK communication system detects a frequency offset between a carrier and a local oscillated signal for adjustment of a local oscillation frequency. A phase difference detector (32) generates a first phase difference detection signal having a difference between the phases of the sampled signals as a phase value. A phase altering portion (34, 50) generates a second phase difference detection signal having a phase value different from that of the first phase difference detection signal. A frequency offset signal generator (36, 38, 61, 62, 63, 64) estimates transmission phase information by using a phase value of the second phase difference detection signal and reference phase signals used for the MPSK modulation, thereby generating a frequency offset signal which is determined by the transmission phase signal and the second phase difference detection signal. The number of the reference phases which are used for determination of the transmission phase information by altering the phase of the phase difference signal, is reduced. Accordingly, the cost of the hardware of the actually implemented apparatus can be lowered. Such a technology can be used for the automatic frequency control for a modem which is used for all the types of the MPSK modulation.

Description: Field of the Invention The present invention relates to an automatic frequency control method and an apparatus therefor, and more particularly, to an automatic frequency control technology which is used for detecting syncs from a signal which is M-ary phase-shift-keying (MPSK) modulated and transmitted. Description of Related Art In the communication technology field, a receiver adopting a sync detection method detects a sync from a received signal and then performs demodulation of the signal. It is possible to perfectly detect the sync from the received signal and to perfectly demodulate the received signal into an original signal, when both the frequency and the phase of a local carrier signal are the same as those of a modulated carrier signal. Thus, both the frequency and the phase of a local carrier signal should be synchronized with those of a modulated carrier signal, respectively. A conventional technology for detecting the sync from the received signal will be described below with reference to Figures 1, 2A and 2B. Figure 1 shows an automatic frequency control apparatus for general quadrature phase-shift-keying (QPSK) demodulation. In Figure 1, a received signal is input to multipliers 11 and 12. Each of multipliers 11 and 12 multiplies the received signal by an output of a voltage controlled oscillator 19. Multipliers 11 and 12 generate signals of which the phases are different from each other by 90°. The output of multiplier 11 or 12 is low-frequency-converted into a baseband signal by a low-pass filter 13 or 14. When the received signal does not include the Gaussian noise, the former can be expressed as the following equation: S(t)=Acos(ω 0 t+ϕ(t)) . Here, S(t) is a function of a received signal at time t, A is an amplitude, ω 0 is a frequency, and ϕ (t) is a function of a phase at time t. In this case, low-pass filter 13 generates an in-phase (I) channel signal which is represented as an equation: I(t)=Acos(Δωt+ϕ(t)) . On the other hand, low-pass filter 14 generates a quadrature (Q) channel signal which is represented as an equation: Q(t)=Asin(Δωt+ϕ(t)) . Here, A is an amplitude, Δω is a frequency difference, and ϕ(t) is a function of a phase at time t. Signals I(t) and Q(t) after passing through low-pass filters 13 and 14 are digitally converted by analog-to-digital converters 15 and 16, respectively. The output signals I k and Q k of analog-to-digital converters 15 and 16 are transmitted for signal demodulation and simultaneously supplied to a frequency detector 17. The output signals I k and Q k of analog-to-digital converters 15 and 16 have a phase ϕ(t) which is varied every symbol period T b , respectively. For example, in the case of the QPSK method, phase ϕ(t) has one value of 45°, 135°, -45° and -135°, which is varied every symbol period of T b according to bit-stream information of a transmitter end. Frequency detector 17 receives two channel signals I k and Q k and then generates a frequency offset signal V(k). Frequency offset signal V(k) is generated when a local oscillated frequency does not match the frequency of the received signal in an actual apparatus. Frequency offset signal V(k) passes through a loop filter 18, and then is supplied to a voltage controlled oscillator (VCO) 19, VCO 19 generates signals having respectively different local oscillated frequencies according to the input frequency offset signal V(k). The local oscillated signals are supplied to multipliers 11 and 12, and used for generating an I-channel signal and a Q-channel signal having a 90° phase difference from each other. By repeating such a process, both the frequency and the phase of the internal oscillated signal are synchronized with those of the received signal. The technologies of detecting the frequency offset information are described in the following references: [1] AFC Tracking Algorithms (IEEE trans, on communications, vol COM-32, No. 8, August 1984, pp 935-947); and [2] A New QPSK Demodulator for Digital DBS Receivers (IEEE 1922 pp. 192-193). Figure 2A shows a circuit which adopts a cross-product disclosed in the above reference [1] as frequency detector 17 of Figure 1. When the sampled and digitally converted I-channel and Q-channel signals I k and Q k are input to the Figure 2 circuit, I-channel signal I k is supplied to a delay 21 and multiplier 24, while Q-channel signal Q k is supplied to a delay 22 and multiplier 23. Multiplier 23 multiplies the delayed I channel signal I k-1 by Q-channel signal Q k while multiplier 24 multiplies the delayed Q-channel signal Q k-1 by I-channel signal I k . A subtracter 25 subtracts output signal I k ·Q k-1 of multiplier 24 from output signal Q k ·I k-1 of multiplier 23. Subtracter 25 generates frequency offset signal V(k) which is determined by sampling period T s and symbol period T b . When sampling period T s equals symbol period T b subtracter 25 generates frequency offset signal V(k) according to the following equation (1). V(k)=A 2 sin(ΔωT s + k ) Here, Δω=ω 1 -ω 0 , ϕ (t) = ϕ k , kT s ≤ t ≤ (k-l) T s , and  k =ϕ k -ϕ k-l . When T s <T b (=nT s ), that is, when the input signal is oversampled, frequency offset signal V(k) generated by subtracter 25 is expressed as the following equation (2). V(k)=A 2 sin(ΔωT s ), if k≠nℓ (ℓ is an integer), and V(k)=A 2 sin(ΔωT s + l ), if k=nℓ (ℓ is an integer) Figure 2B shows a frequency detector using an arc-tangent disclosed in reference [2]. Arc-tangent portion 27 received two channel signals I k and Q k and performs an arc-tangent operation using Q-channel signal Q k as a numerator and I-channel signal I k as a denominator. A differentiator 28 generates frequency offset signal V(k) which is expressed as the following equations (3) and (4), from the output signal of arc-tangent portion 27. V(k)=ΔωT s +  k V(k)=ΔωT s , if k≠nℓ (ℓ is an integer), and V(k)=ΔωT s +  ℓ if k=nℓ; (ℓ is an integer) The above equation (3) represents an output signal of differentiator 28 when T s =T b . The above equation (4) represents an output signal of differentiator 28 when T s <T b (=nT s ), that is, when the signal is oversampled. To detect an exact frequency, it is not desirable to include terms of  k and  l of which the values are varied according to the transmitted information. However, as it can be seen from the above equations (1) and (3), when the sampling frequency equals a symbol rate, frequency offset signal V(k) includes a transmission phase value  k . Therefore, it becomes impossible to detect an exact frequency which is proportional to only frequency offset information ΔωT. Also, when the oversampled sample has symbol transition, transmission phase value  k exists in frequency offset signal V(k), which interferes with the exact frequency detection. Although the performance of the frequency detection can be enhanced according to a degree of oversampling thereof, it causes cost increase of the hardware for oversampling when the symbol rate is more than 20MHz as in a direct broadcasting satellite (DBS). Such a problem occurs in a differentiator automatic frequency control apparatus and a discrete Fourier transform automatic frequency control apparatus too. European Patent Application 0491403 A2 discloses a method and device for estimating the carrier frequency of a digital signal. The method involves two estimates of the carrier phase being performed in successive instants, and the estimated carrier frequency is obtained from a comparison of the two estimates. Summary of the Invention It is an aim of embodiments of the present invention to provide an automatic frequency control method for detecting frequency offset information, and particularly reducing the number of reference phases which are used for phase detection of a transmitted signal by altering a phase difference between sampled signals which are detected from a phase shift-keying modulated signal into another phase difference and determining a phase of the transmitted signal by using the altered phase difference. It is another aim of embodiments of the present invention to provide an automatic frequency control apparatus for detecting frequency offset information, and particularly reducing the number of reference phases which are used for phase detection of a transmitted signal, by determining a phase of the transmitted signal with an altered phase difference obtained by altering a phase difference between phase-shift-keying modulated signals. According to the present invention, there is provided an automatic frequency control method for receiving an M-ary phase-shift-keying modulated signal, detecting a frequency offset signal and controlling an oscillated frequency based on the detected frequency offset signal, the automatic frequency control method comprising the steps of: sampling the received signal with a predetermined sampling frequency and generating a sampled complex signal; detecting a phase difference value between the currently sampled complex signal and the stored previous sampled complex signal, to generate a first phase difference detection signal of which the phase value is the detected phase difference value; altering the detected phase difference value of the first phase difference detection signal by a phase altering factor, to generate a second phase difference detection signal of which the phase value is the altered phase difference value; determining transmission phase information which the altered phase difference value has, by using the altered phase difference value of the second phase difference detection signal and reference phase values which are used for information transmission in the M-ary phase shift-keying modulation; and generating the frequency offset signal by using the determined transmission phase information and the altered phase difference value. Suitably, said sampling frequency matches a symbol rate of the received signal. Suitably, said first phase difference detection signal generation step generates the first phase difference detection signal U k having the phase difference value ( k +ΔωT) as the phase by calculating the currently sampled complex signal R k and the previously-sampled complex signal R k-1 according to the following equation: U k ≡ R k R * k -1 R k · R k -1 =e j ( k +Δω T ) in which  k is the transmission phase information and ΔωT is the frequency offset signal. Suitably, said first phase difference detection signal generation step generates the first phase difference detection signal U k having the phase difference value ( k +ΔωT) as the phase by calculating the currently sampled complex signal R k and the previously-sampled complex signal R k-1 according to the following equation: U k =R k ·R* k-1 in which R* k-1 is a complex conjugate of R k-1 . Suitably, said second phase difference detection signal generation step generates the second phase difference detection signal having the altered phase difference value obtained by multiplying the phase difference value by the phase altering factor (M/N) being a ratio of the value M of the phase-shift-keying modulated signal and a coefficient N having a relationship of an equation M=lN where l is a positive integer. Suitably, said transmission phase information determination step comprises the substeps of: determining the reference phase values which the altered phase difference value can take among the reference phase values which are used for transmission of the information in the M-ary phase-shift-keying modulation; and comparing the altered phase difference value with the determined reference phase values, to determine the determined reference phase value which is closest to the altered phase difference value among the determined reference phase values as the altered transmission phase information. Suitably, said altered phase difference value comprises the frequency offset signal ([M/N]ΔωT) and the altered transmission phase information ([M/N] k ) which exist within the range: -π/N<[M/N]ΔωT<π/N in which N satisfies a relationship of equation: M= l n where l is a positive integer. Suitably, said frequency offset signal generation step comprises the substeps of: generating the complex signal having the determined transmission phase information; multiplying the complex conjugate of the complex signal by the second phase difference detection signal; and determining the imaginary component signal of the signal obtained by the multiplication as the frequency offset signal. Suitably, said method further comprises the substep of re-determining a value obtained by multiplying an arc-sine value of the imaginary component determined as the frequency offset signal by the phase altering factor, as a frequency offset signal. According to a second aspect of the present invention, there is provided an automatic frequency control apparatus for receiving an M-ary phase-shift-keying modulated signal, detecting a frequency offset signal and controlling an oscillated frequency based on the detected frequency offset signal, said automatic frequency control apparatus comprising: means for sampling the received signal with a predetermined sampling frequency and generating a currently sampled complex signal; phase difference detection means for receiving the currently sampled signal and detecting a phase difference value between the currently sampled complex signal and the stored previous sampled complex signal, to generate a first phase difference detection signal of which the phase value is the detected phase difference value; phase difference altering means for receiving the first phase difference detection signal and altering the detected phase difference value of the first phase difference detection signal by a phase altering factor, to generate a second phase difference detection signal of which the phase value is the altered phase difference value; and means for determining transmission phase information which the altered phase difference value has by using the altered phase difference value of the second phase difference detection signal and reference phase values which are used for information transmission in the M-ary phase-shift-keying modulation, and for generating the frequency offset signal by using the determined transmission phase information and the altered phase difference value. Suitably, said sampling means samples the received signal with a sampling frequency which matches a symbol rate of the received signal. Suitably, said phase difference detection means normalizes the currently sampled complex signal and the previously sampled complex signal, and generates the first phase difference detection signal having the phase difference value detected by the normalization. Suitably, said phase difference detection means complex conjugate-operates the currently sampled complex signal and the previously sampled complex signal, and generates the first phase difference detection signal having the phase difference value detected by the complex-conjugate-operation. Suitably, said phase difference altering means generates the second phase difference detection signal having the altered phase difference value obtained by multiplying the detected phase difference value which the first phase difference detection signal has, by the phase altering factor (M/N) in which the value M of the phase-shift-keying modulated signal is a numerator and a coefficient N having a relationship of an equation M= IN where l is a positive integer is a denominator. Suitably, said frequency offset signal generation means comprises a first frequency offset signal generator for determining the reference phase value in which a difference between the reference phase values and the altered phase difference value used for the information transmission in the M-ary phase-shift-keying modulation exists in the range: - π/N<[M/N]ΔωT<π/N in which the value M of the M-ary phase-shift-keying modulated signal is a numerator and a coefficient N satisfying an equation: M= l N where l is a positive integer is a denominator, and generating the complex signal having the determined altered transmission phase information, and for multiplying the complex conjugate of the complex signal by the second phase difference detection signal, thereby generating the imaginary component signal of the signal obtained by the multiplication as the frequency offset signal. Suitably, said apparatus further comprises a second frequency offset signal generator for generating a new frequency offset signal by multiplying the arc sine value of the frequency offset signal generated by said first frequency offset signal generator by the phase altering factor. Suitably, said apparatus further comprises phase difference altering means for receiving the first phase difference detection signal and altering the detected phase difference value of the first phase difference detection signal by a phase altering factor M/2 with respect to the value M of the M-ary phase-shift-keying modulated signal, means for receiving the second phase difference detection signal and determining transmission phase information Ø which the altered phase difference value has, by using the altered phase difference value of the second phase difference detection signal and reference phase values which are used for information transmission in the M-ary phase shift-keying modulation, and for multiplying the second phase difference detection signal by complex signal e -jΨ having the transmission phase information to generate the frequency offset signal based on a sign of the C k among the imagainary component of the signal obtained by multiplication. Suitably, said frequency offset signal generation means determines imaginary component signal S k as the frequency offset signal when real component signal C k is greater than zero, while determining imaginary component signal -S k as the frequency offset signal when real component signal C k is less than zero. Suitably, said apparatus further comprises means for generating a new frequency offset signal by eradicating the phase altering factor M/2 and a sine function component which are included in the imaginary component signal S k . Suitably, said apparatus further comprises phase difference altering means for receiving the first phase difference detection signal and altering the detected phase difference value of the first phase difference detection signal by using a phase altering factor M/4 with respect to the M of the M-ary phase-shift-keying modulated signal, to generate a second phase difference detection signal ( U k M/4 =C k +jS k ) of which the phase value is the altered phase difference value ([M/4]( k +ΔωT)); and means for receiving the second phase difference detection signal and generating the frequency offset signal by using the real and imaginary components of the second phase difference detection signal. Suitably, said frequency offset signal generation means comprises: a first sign generator for generating a first sign signal being a value of a signum function obtained by subtracting an imaginary component of the second phase difference detection signal from a real component thereof; a second sign generator for generating a second sign signal being a value of a signum function obtained by adding the real and imaginary components; a subtracter for subtracting the second sign signal from the first sign signal; a first adder for adding the first and second sign signals; a third sign generator for outputting a value of a signum function of the signal applied from the subtracter; a fourth sign generator for outputting a value of a signum function of the signal applied from the first adder; a first multiplier for multiplying a first component signal by the output signal from said third sign generator; a second multiplier for multiplying a second component signal by the output signal from said fourth sign generator; and a second adder for adding the output signals of said first and second multipliers and generating a frequency offset signal. Suitably said apparatus further comprises means for generating a new frequency offset signal by multiplying an arc-sine value of the frequency offset signal generated by said frequency offset signal generation means by the phase altering factor. The automatic frequency control apparatus according to the present invention uses a signal which is sampled with a sampling frequency which matches a symbol rate of the received signal. Brief Description of the Drawings Preferred embodiments of the present are described by way of example only, with reference to the drawings, wherein: Figure 1 is a block diagram of an automatic frequency control apparatus for general quadrature phase-shift-keying (QPSK) demodulation. Figures 2A and 2B are schematic diagrams of conventional frequency detectors. Figure 3 is a block diagram of a frequency detector according to a preferred embodiment of the present invention. Figure 4 is a graphic diagram for explaining determination of transmission phase information of the frequency detector shown in Figure 3. Figure 5 is a graphic diagram of discriminating curves for illustrating the frequency offset information of Figure 3. Figure 6 is a block diagram of a frequency detector according to another preferred embodiment of the present invention. Figure 7 is a graphic diagram for explaining determination of transmission phase information of the frequency detector shown in Figure 6. Figure 8 is a graphic diagram of discriminating curves for illustrating the frequency offset information of Figure 6. Detailed Description of the Preferred Embodiments Preferred embodiments of the present invention will be described below in more detail with reference to the accompanying drawings Figures 3 through 8. Figure 3 shows a frequency detector according to a preferred embodiment of the present invention. The Figure 3 apparatus includes a sampling portion 30, a phase difference detector 32, a phase altering portion 34 and frequency offset signal generators 36 and 38. The M-ary PSK modulated signal has transmission phase information  k which is varied according to the transmitted information. The transmission phase information  k becomes one of a plurality of reference phases Ψ i for transmission of the PSK modulated information. If the MPSK modulated signal is received, a receiver (not shown) demodulates the received signal. Sampling portion 30 samples the input signal with a sampling frequency which is equal to a symbol rate and outputs the sampled result. The currently sampled signal R k includes noise and frequency offset information ΔωT, and can be expressed as the following equation (5) when the magnitude r k ' is varied due to the noise. R k ≡ I k + jQ k = r k '· e j(ψ k + ΔωT k ) If the currently sampled complex signal R k is applied to phase difference detector 32, phase difference detector 32 normalizes the sampled complex signal R k according to the following equation (6), to generate a first phase difference detection signal U k . That is, using the stored previously-sampled complex signal R k-1 , the currently sampled complex signal R k is normalized to generate first phase difference detection signal U k . U k ≡ R k R * k -1 R k · R k -1 = e j (ψ k -ψ k -1 +Δω T ) = e j ( k +Δω T ) = C k + jS k Here, C k is a real component signal, S k is an imaginary component signal. As it can be seen from equation (6), first phase difference detection signal U k is a signal in which a magnitude of the distorted signal due to the noise is compensated. The present invention is not limited to an operation of the normalization by phase difference detector 32. Thus, it is possible for phase difference detector 32 to generate another first phase difference detection signal U k ' from signals (R k ,R k-1 ) using the relationship of equation U k ' = R k R* k-1 for complex conjugate operation. Further, components 34, 36 and 38 to be described later can be constructed so as to operate well also in case of a new first phase difference detection signal U k '. If the phase difference value of first phase difference detection signal U k is < U k' phase difference value  k + ΔωT which is calculated by the normalization or the complex conjugate operation always satisfies the following equations (7) and (8). ∠U k =  k + Δω T or ΔωT = ∠ U k -  k Thus, if transmission phase information  k which is varied according to the transmitted information is known, it is possible to exactly calculate frequency offset information ΔωT. Generally, transmission phase information  k is not a sequential value, and is quantized with a reference phase of the MPSK so as to be transmitted. Thus, the quantized transmission phase information  k can have reference phase value Ψ i , as can be seen from the following equation (9).  k ∈{ψ i |ψ i =O,±(2/M) π,±(4/M) π,±(6/M) π,.....,±((M-2)/M) π,π; in case of the MPSK} Therefore, when first phase difference detection signal U k has frequency offset information ΔωT within an allowable range in a frequency control apparatus, transmission phase information  k can be exactly detected. However, as a value of M is larger in the above equation (9), a slicer (not shown) being a conventional circuit for estimating transmission phase information  k becomes complicated. To solve such a problem phase altering portion 34 alters to  k +ΔωT of first phase difference detection signal U k using the following equation (10). U k M N = e j M N ( k +Δω T ) = e j ( M N  k + M N Δω T ) ≡ C k + jS k Here, M is a multiple of N, that is, M=ℓN where ℓ is a positive integer. Phase altering portion 34 receives first phase difference detection signal U k and alters the phase difference value expressed as equation (7) into [M/N] ( k + ΔωT), and generates a second phase difference detection signal U k M/N . Thus, if [M/N] ( k +ΔωT) exists within a range expressed as the following equation (11), a value Ψ i of the altered transmission phase information [M/N] k can be estimated from the above equation (9). - π N < M N Δω T < π N First frequency offset signal generator 36 receives second phase difference detection signal U k M/N from phase altering portion 34, estimates a value of the altered transmission phase information [M/N] k and generates first frequency offset signal sin([M/N]ΔωT) based on the estimated transmission phase information ψ i . First frequency offset signal sin([M/N]ΔωT) is calculated by the following equation (22). sin ( M N Δω T ) = Im [ U K M N · e - j ψ i ] = S k cosψ i - C k sinψ i Thus, a person skilled in the art which is related to the present invention can obtain frequency offset signal generators of a variety of types which embody equation (12) which use second phase difference detection signal U k M/N and estimated transmission phase information ψ i , within the scope of the present invention. For explanation of a more specific example, an operation of a first frequency offset signal generator 36 when N=2 and M≥N, will be described below with reference to Figure 4. A reference phase Ψ i which the altered transmission phase information [M/2] k can take when N=2, is one of Ψ 0 =0 and Ψ 1 =π from the above equation (9). Such a reference phase Ψ i is shown in Figure 4. Thus, when frequency offset information ([M/2]ΔωT) exists within a range expressed as the following equation (13), first frequency offset signal generator 36 uses the input altered phase difference value ∠U k M/2 and can estimate the altered transmission phase information ([M/2] k ). - π 2 < M 2 Δω T < π 2 Phase altering portion 34 which is appropriately constructed when N=2 outputs phase difference detection signal U k M/2 as a pattern of a real component signal C k,2 and an imaginary component signal S k,2 and imaginary component signal S k,2 to generate frequency offset signal sin([M/2]ΔωT) . At the beginning, first frequency offset signal generator 36 judges a sign of the input real components signal C k,2 to determine the altered transmission phase information ( [M/2]  k ) . If real component signal C k,2 has a positive value, a reference phase ψ 0 of transmission phase information ([M/2] k ) has a value of zero, while if real component signal C k,2 has a negative value, a reference phase Ψ i of transmission phase information ([M/2] k ) has a value of π. By the equation (12), when ( [M/2]  k ) =0, sin ( [M/2] ΔωT) equals S k , while when ([M/2] k ) = π, sin([M/2]ΔωT) equals -S k . Thus, first frequency offset signal generator 36 generates frequency offset signal sin([M/2]ΔωT) of S k2 or -S k2 which is determined by a sign of real component signal C k,2 . Even when only first frequency offset signal sin([M/N]ΔωT) will be used, an exact frequency offset information which does not include the transmission phase information can also be obtained. However, to eradicate a sine function which is included in first frequency offset signal sin([M/N]ΔωT) , second frequency offset signal generator 38 is additionally used. If first frequency offset signal generator 36 generates first frequency offset signal sin([M/N]ΔωT), second frequency offset signal generator 38 generates second frequency offset signal ΔωT, using the following equation (14). Δω T = M N sin -1 ( S k cosψ i - C k sinψ i ) First frequency offset signal sin ( [M/2] ΔωT) or second frequency offset signal ΔωT is used for sync detection of the receiver. Figure 6 shows a frequency detector according to another preferred embodiment of the present invention. The Figure 6 apparatus is one implemented when N=4 and M≥N in the above equation (10). In Figure 6 sampling portion 30 and phase difference detector 32 perform the same functions as those of the corresponding blocks of the same reference numerals shown in Figure 3. Accordingly, the detailed descriptions thereof will be omitted. Phase altering portion 50 which receives first phase difference detection signal U k uses the above equation (10) to generate phase difference detection signal U k M/4 having the altered phase difference value [M/4]( k +ΔωT) from phase difference detection signal U k having phase difference value ∠U k . Phase altering portion 50 ouputs phase difference detection signal U k M/4 as a pattern of a real component signal C k,4 and an imaginary component signal S k,4 . A third frequency offset signal generator 60 includes sign generators 61, 62, 65 and 66, subtracter 63, adders 64 and 69 and multipliers 67 and 68. Third frequency offset signal generator 60 receives real component signal C k,4 and imaginary component signal S k,4 to determine the altered transmission phase information [M/4] k , and to then generate frequency offset signal sin([M/4]ΔωT) . When N=4 reference phase Ψ i , satisfying the above equations (9) and (10) is expressed as four values as seen in the following equation (15). M 4  k ∈{ψ i |ψ i =0,± π 2 ,π} That is, reference phase ψ i , which the transmission phase information [M/4] k can take when N=4, is one of Ψ 0 =0 , Ψ 1 =π/2 , Ψ 2 =π and Ψ 3 =-π/2 from the above equation (15). Such a reference phase Ψ i is shown in Figure 7. Thus, when frequency offset information ([M/4]ΔωT) exists within a range expressed as the following equation (16), third frequency offset signal generator 60 uses the input altered phase difference value ∠U k M/4 and can estimate the altered transmission phase information ([M/4] k ) - π 4 < M 4 Δω T < π 4 Real component signal C k,4 and imaginary component signal S k,4 from phase altering portion 50 are applied to first and second sign generators 61 and 62. Also, real component signal C k,4 is applied to first multiplier 67, and imaginary component signal S k,4 is applied to second multiplier 68. First sign generator 61 generates a first sign signal being a value of a signum function with respect to difference C k,4 -S k,4 between real component signal C k,4 and imaginary component signal S k,4 while second sign generator 62 generates a second sign signal being a value of a signum function with respect to sum C k,4 +S k,4 of real component signal C k,4 and imaginary component signal S k,4 . Subtracter 63 receives the first and second sign signals and subtracts the second sign signal from the first sign signal, thereby outputting the result. First adder 64 receives the first and second sign signals and adds the second sign signal to the first sign signal, thereby outputting the result. Third sign generator 65 receives the output signal of subtracter 63 to generate a third sign signal being a value of a signum function. Fourth sign generator 66 receives the output signal of subtracter 63 to generate a fourth sign signal being a value of a signum function. First multiplier 67 receives the third sign signal and real component signal C k,4 and multiplies the received signals by each other to output the result, while second multiplier 68 receives the fourth sign signal and imaginary component signal S k,4 and multiplies the received signals by each other to output the result. Second adder 69 receives the output signals of multipliers 67 and 68 and multiplies the received signals by each other to generate frequency offset signal sin([M/4]ΔωT) . Fourth frequency offset signal generator 70 is obtained by embodying the following equation (17) and receives the first frequency offset signal to generate second frequency offset signal ΔωT. Δω T = 4 M sin -1 ( S k COS ψ i - C k sinψ i ) Frequency offset signal sin([M/4]ΔωT) or ΔωT is used for sync detection of the receiver. Figures 5 and 8 show discriminating curves for illustrating the frequency offset signals which are generated by frequency offset signal generators 36, 38, 60 and 70 of Figures 3 and 6, respectively. The characteristic curves of Figures 5 and 8 are obtained by discriminators (not shown) under the conditions of |ΔωT|<π/M,|Δf s |<f s /2M , and f s =1/T b . The Figures 5 and 8 curves obtained by the discriminators have a curve "A" for frequency offset signal sin([M/4]ΔωT) and a curve "B" for frequency offset signal ΔωT. The discriminator curve "A" becomes non-linear near a boundary point π/M. However, since the discriminator "A" is useful for detecting the frequency offset information in the actual apparatus frequency offset signal sin([M/4]ΔωT) can be used as the frequency offset information. If frequency offset signal ΔωT is used, it is possible to detect more exact frequency offset information although an amount of the calculation increases. The present invention detects a frequency offset signal which is generated by mismatching between the carrier frequency and the local oscillated frequency or by the Doppler-shift, in the MPSK communication system. Particularly, the signal which is sampled with a sampling frequency corresponding to the symbol rate is used. As a method for altering the detected phase difference value, the number of the reference phases which are used for determination of the transmission phase information is decreased. Accordingly, the present invention can lower the cost of the hardware of the apparatus implemented. The present invention can be used for automatically controlling frequencies in a modem which uses all the types of the MPSK modulation. While only certain embodiments of the invention have been specifically described herein, it will be apparent to the skilled addressee that various modifications may be made thereto without departing from the scope of the invention as defined in the appended claims.

Claims: An automatic frequency control method for receiving an M-ary phase-shift keying modulated signal, detecting a frequency offset signal and controlling an osuillated frequency based on the detected frequency offset signal, said automatic frequency control method comprising the steps of: sampling the received signal with a predetermined sampling frequency and generating a sampled complex signal; detecting a phase difference value between the currently sampled complex signal and the stored previous sampled complex signal, to generate a first phase difference detection signal of which the phase value is the detected phase difference value; altering the detected phase difference value of the first phase difference detection signal by a phase altering factor, to generate a second phase difference detection signal of which the phase value is the altered phase difference value; determining transmission phase information which the altered phase difference value has, by using the altered phase difference value of the second phase difference detection signal and reference phase values which are used for information transmission in the M-ary phase-shift keying modulation; and generating the frequency offset signal by using the determined transmission phase information and the altered phase difference value. An automatic frequency control method according to claim 1, wherein said sampling frequency matches a symbol rate of the received signal. An automatic frequency control method according to claim 1 or claim 2, wherein said first phase difference detection signal generation step generates the first phase difference detection signal U k having the phase difference value ( k +ΔωT) as the phase by calculating the currently sampled complex signal R k and the previously-sampled complex signal R k-1 according to the following equation: U k ≡ R k R* k-1 R k • R k -1 =e j( k +ΔωT) in which  k is the transmission phase information and ΔωT is the frequency offset signal. An automatic frequency control method according to claim 1 or claim 2, wherein said first phase difference detection signal generation step generates the first phase difference detection signal U k having the phase difference value ( k +ΔωT) as the phase by calculating the currently sampled complex signal R k and the previously-sampled complex signal R k-1 according to the following equation: U k =R k R* k-1 in which R* k-1 is a complex conjugate of R k-1 . An automatic frequency control method according to any preceding claim, wherein said second phase difference detection signal generation step generates the second phase difference detection signal having the altered phase difference value obtained by multiplying the phase difference value by the phase altering factor CM/N) being a ratio of the value N of the phase-shift-keying modulated signal and a coefficient N having a relationship of an equation M=lN where l is a positive integer. An automatic frequency control method according to any preceding claim, wherein said transmission phase information determination step comprises the substeps of: determining the reference phase values which the altered phase difference value can take among the reference phase values which are used for transmission of the information in the M-ary phase-shift-keying modulation; and comparing the altered phase difference value with the determined reference phase values, to determine the determined reference phase value which is closest to the altered phase difference value among the determined reference phase values as the altered transmission phase information. An automatic frequency control method according to claim 6, wherein said altered phase difference value comprises the frequency off set signal ([M/N]ΔωT) and the altered transmission phase information ([M/N] k ) which exist within the range: -π/N < [M/N] ΔωT < π/N in which N satisfies a relationship of equation: M= l n where l is a positive integer. An automatic frequency control method according to any preceding claim, wherein said frequency offset signal generation step comprises the substeps of: generating the complex signal having the determined transmission phase information; multiplying the complex conjugate of the complex signal by the second phase difference detection signal; and determining the imaginary component signal of the signal obtained by the multiplication as the frequency offset signal. An automatic frequency control method according to claim 8, further comprising the substep of re-determining a value obtained by multiplying an arc-sine value of the imaginary component determined as the frequency offset signal by the phase altering factor, as a frequency offset signal. An automatic frequency control apparatus for receiving an M-ary phase-shift-keying modulated signal, detecting a frequency offset signal and controlling an oscillated frequency based on the detected frequency offset signal, said automatic frequency control apparatus comprising: means (30) for sampling the received signal with a predetermined sampling frequency and generating a currently sampled complex signal; phase difference detection means (32) for receiving the currently sampled signal and detecting a phase difference value between the currently sampled complex signal and the stored previous sampled complex signal, to generate a first phase difference detection signal of which the phase value is the detected phase difference value; phase difference altering means (34) for receiving the first phase difference detection signal and altering the detected phase difference value of the first phase difference detection signal by a phase altering factor, to generate a second phase difference detection signal of which the phase value is the altered phase difference value; and means (36, 38) for determining transmission phase information which the altered phase difference value has by using the altered phase difference value of the second phase difference detection signal and reference phase values which are used for information transmission in the M-ary phase-shift-keying modulation, and for generating the frequency offset signal by using the determined transmission phase information and the altered phase difference value. An automatic frequency control apparatus according to claim 10, wherein said sampling means (30) samples the received signal with a sampling frequency which matches a symbol rate of the received signal. An automatic frequency control apparatus according to claim 10 or claim 11, wherein said phase difference detection means (34) normalizes the currently sampled complex signal and the previously sampled complex signal, and generates the first phase difference detection signal having the phase difference value detected by the normalization. An automatic frequency control apparatus according to claim 10 or claim 11, wherein said phase difference detection means (34) complex conjugate-operates the currently sampled complex signal and the previously sampled complex signal, and generates the first phase difference detection signal having the phase difference value detected by the complex-conjugate-operation. An automatic frequency control apparatus according to any one of claims 10 to 13, wherein said phase difference altering means (34) generates the second phase difference detection signal having the altered phase difference value obtained by multiplying the detected phase difference value which the first phase difference detection signal has, by the phase altering factor (M/N) in which the value M of the phase-shift-keying modulated signal is a numerator and a coefficient N having a relationship of an equation M=IN where I is a positive integer is a denominator. An automatic frequency control apparatus according to any one of claims 10 to 14, wherein said frequency offset signal generation means (36, 36) comprises a first frequency offset signal generator (36) for determining the reference phase value in which a difference between the reference phase values and the altered phase difference value used for the information transmission in the M-ary phase-shift-keying modulation exists in the range: -π/N < [M/N]ΔωT < π/N in which the value N of the M-ary phase-shift-keying modulated signal is a numerator and a coefficient N satisfying an equation: M=lN where l is a positive integer is a denominator, and generating the complex signal having the determined altered transmission phase information, and for multiplying the complex conjugate of the complex signal by the second phase difference detection signal, thereby generating the imaginary component signal of the signal obtained by the multiplication as the frequency offset signal. An automatic frequency control apparatus according to claim 15, further comprising a second frequency offset signal generator (38) for generating a new frequency offset signal by multiplying the arc sine value of the frequency offset signal generated by said first frequency offset signal generator (36) by the phase altering factor. An automatic frequency control apparatus as claimed in any one of claims 10 to 16 wherein phase difference altering means (34) for receiving the first phase difference detection signal and altering the detected phase difference value of the first phase difference detection signal by a phase altering factor M/2 with respect to the value M of the M-ary phase-shift-keying modulated signal to generate a second phase difference detection signal ( U k M/2 =C k +jS k ) of which the phase value is the altered phase difference value ([M/2]( k +ΔωT)); and means (36, 38) for receiving the second phase difference detection signal and determining transmission phase information Ψ which the altered phase difference value has, by using the altered phase difference value of the second phase difference detection signal and reference phase values which are used for information transmission in the M-ary phase shift keying modulation, and for multiplying the second phase difference detection signal by complex signal e -j Ψ having the transmission phase information to generate the frequency offset signal based on a sign of the C k among the imaginary component (S k cosΨ-C k sinΨ) of the signal obtained by the multiplication. An automatic frequency control apparatus according to claim 17, wherein said frequency offset signal generation means (36, 38) determines imaginary component signal S k as the frequency offset signal when real component signal C k is greater than zero, while determining imaginary component signal -S k as the frequency offset signal when real component signal C k is less than zero. An automatic frequency control apparatus according to claim 18, further comprising means (36, 38) for generating a new frequency offset signal by eradicating the phase altering factor M/2 and a sine function component which are included in the imaginary component signal S k . An automatic frequency control apparatus as claimed in any one of claims 10 to 16, wherein phase difference altering means (50) for receiving the first phase difference detection signal and altering the detected phase difference value of the first phase difference detection signal by using a phase altering factor M/4 with respect to the N of the M-ary phase-shift-keying modulated signal, to generate a second phase difference detection signal ( Uk M/4 =C k +jS k ) of which the phase value is the altered phase difference value ([M/4]( k +ΔωT)); and means (60, 70) for receiving the second phase difference detection signal and generating the frequency offset signal by using the real and imaginary components of the second phase difference detection signal. An automatic frequency control apparatus according to claim 20, wherein said frequency offset signal generation means (60, 70) comprises: a first sign generator (61) for generating a first sign signal being a value of a signum function obtained by subtracting an imaginary component of the second phase difference detection signal from a real component thereof; a second sign generator (62) for generating a second sign signal being a value of a signum function obtained by adding the real and imaginary components; a subtracter (63) for subtracting the second sign signal from the first sign signal; a first adder (64) for adding the first and second sign signals; a third sign generator (65) for outputting a value of a signum function of the signal applied from the subtracter (63) a fourth sign generator (66) for outputting a value of a signum function of the signal applied from the first adder (64) a first multiplier (67) for multiplying a first component signal by the output signal from said third sign generator (65) a second multiplier (68) for multiplying a second component signal by the output signal from said fourth sign generator (66); and a second adder (69) for adding the output signals of said first (67) and second (68) multipliers and generating a frequency offset signal. An automatic frequency control apparatus according to claim 21 further comprising means (70) for generating a new frequency offset signal by multiplying an arc-sine value of the frequency offset signal generated by said frequency offset signal generation means (GO, 70) by the phase altering factor.

Inventors: CHOI YANG-SEOK, CHOI, YANG-SEOK
Applicants: SAMSUNG ELECTRONICS CO LTD, SAMSUNG ELECTRONICS CO., LTD.
Application year: 1995
Main classification: H04L27
IPC codes: H04L27, H03J7